1981_Plessey_Television_IC_Handbook 1981 Plessey Television IC Handbook
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Television
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• Plessey Semiconductors
TELEVISION
Ie I-IANDBOOK
APRIL 1981
•
Plessey
Semiconductors
1641 Kaiser Avenue
Irvine, CA. 92714
$3.50
PSI 1775
This pulication is issued to provide outline information only and (unless specifically agreed to the contary by
the Company in writing) is not to form part of any order or contract or be regarded as representation relating
to the products or services concerned. We reserve the right to alter without notice the specification, design,
price or conditions of supply of any product or service.
2
Contents
1.
PRODUCT RANGE INFORMATION ........................................... 7-26
2.
TV FREQUENCY SYNTHESISER APPLICATIONS ............................. 27-42
3.
INFRA-RED REMOTE CONTROL APPLICATIONS ............................ 43-50
4.
REMOTE CONTROL FOR TOYS APPLICATIONS ............................. 51-64
5.
ELECTRONIC TOUCH CONTROL APPLICATIONS ........................... 65-76
6.
REMOTE CONTROL USING PPM ............................................ 77-94
7.
TECHNICAL DATA ......................................................... 99-268
8.
PACKAGES ............................................................... 269-278
9.
PLESSEY SEMICONDUCTORS WORLD WiDE .............................. 279-284
3
4
CT2010
1GHz
CT2012
PLL Synthesiser for TV ............................................................... 103
-7
380/400 Prescaler ............................................................. 101
CT2017
Synthesiser Tuning Interface .......................................................... 109
CT2200
5-Bit Binary to 13-Segment Decoder/Driver ............................................ 113
ML231 B
MOS Touch Tuner .................................................................... 117
ML232B
MOS Touch Tuner .................................................................... 119
ML236B
6-Channel Cascadable Touch Control Interface ........................................ 121
ML237B
6-Channel Touch Control Interface .................................................... 125
ML238B
8-Channel Touch Control Interface .................................................... 127
ML239B
8-Channel Touch Control Interface .................................................... 131
ML920
Remote Control Receiver .............................................................. 133
ML922
Remote Control Receiver .............................................................. 137
ML923
Remote Control Receiver .............................................................. 139
ML924
Remote Control Receiver .............................................................. 143
ML925
Remote Control Receiver for Toys ..................................................... 147
ML926
Remote Control Receivers (with momentary outputs) ................................... 151
ML927
Remote Control Receivers (with momentary outputs) ................................... 151
ML928
Remote Control Receivers (with latched outputs) ....................................... 153
ML929
Remote Control Receivers (with latched outputs) ....................................... 153
SL470
BCD to 1 of 10 Decoder/Varicap Driver ................................................ 157
SL480
Infra-red Pulse Pre-Amplifier .......................................................... 159
SL490
Remote Control Transmitter ........................................................... 163
SL952
UHF Amplifier ........................................................................ 167
SL 1430
TV IF Pre-Amplifier ................................................................... 169
SL1431
TV IF Pre-Amplifier with AGC Generator ............................................... 173
SL 1432
TV IF Pre-Amplifier with AGC Generator ............................................... 173
SL 1440
Parallel Sound & Vision IF Amplifiers & Detectors ...................................... 177
SP4020
VHF/UHF
-7
64 Prescalers ............................................................. 179
SP4021
VHF/UHF
-7
64 Prescalers ............................................................. 179
SP4040
VHF/UHF
-7
256 Prescalers ............................................................ 183
SP4041
VHF/UHF
-7
256 Prescalers ............................................................ 183
SW150
Surface Acoustic Wave Color TV IF Filters ............................................. 187
SW153
Surface Acoustic Wave Color TV IF Filters ............................................. 187
SW170
Surface Acoustic Wave Color TV IF Filters ............................................. 187
SW173
Surface Acoustic Wave Color TV IF Filters ............................................. 187
SW200
Surface Acoustic Wave Color TV IF Filters ............................................. 187
SW250
SW400
Surface Acoustic Wave Color TV IF Filters ............................................. 187
Surface Acoustic Wave Color TV IF Filters ............................................. 187
SW450
Surface Acoustic Wave Color TV IF Filters ............................................. 187
TBA120S
Limiting IF Amplifier/FM Detector ..................................................... 197
TBA120T
FM IF Amplifier & Demodulator ........................................................ 201
TBA120U
FM IF Amplifier & Demodulator ........................................................ 201
TBA440N/P
Video IF Amplifier Demodulator ....................................................... 205
TBA530
RGB Matrix Pre-Amplifier ............................................................. 209
5
6
TBA540
Reference Combination ............................................................... 213
TBA560C
TBA800
5W Audio Amplifier .................................................. , ................ 221
Luminance & Chrominance Control Combination ....................................... 217
TBA920
Line Oscillator Combination ........................................................... 225
TBA920S
Line Oscillator Combination ........................................................... 225
TBA950:2X
Line Oscillator Combination .......................................................... 229
TCA800
Color Demodulator with Feedback Clamps ............................................. 233
TDA440
Video IF Amplifier/Demodulator ....................................................... 237
TDA2522
TDA2523
Color Demodulator Combination ...................................................... 241
Color Demodulator Combination ...................................................... 241
TDA2530
RGB Matrix Pre-Amplifier (with clamps) ............................................... 245
TDA2532
RGB Matrix Pre-Amplifier (with clamps) ............................................... 245
TDA2540
Television IF Amplifier & Demodulator ................................................. 249
TDA2541
Television IF Amplifier & Demodulator ................................................. 249
TDA2560
Luminance & Chrominance Control Combination ....................................... 253
TDA2590
TDA2591
Line Oscillator Combination ........................................................... 257
Line Oscillator Combination ........................................................... 263
TDA2593
Line Oscillator Combination ........................................................... 263
1. PRODUCT RANGE
INFORMATION
7
8
Building Block Ie's
Plessey integrated circuits are on the leading edge of
technology without pushing the ragged edge of capability.
We developed the first 2 GHz counter. And a
family of prescalers and controllers for your TV, radio
and instrumentation frequency synthesizers.
We have a monolithic 1 GHz amplifier. And a
complete array of complex integrated function blocks for
radar signal processing and radio communications.
We can supply data conversion devic6S with propagation delays of just 21/2 nanoseconds.
And a range of MNOS logic that stores data for a
year when you remove the power, yet uses only standard
supplies and is fully TTL/CMOS-compatible.
To develop this edge, we developed our own
processes, both bipolar and MOS. The processes were
designed for quality and repeatability, then applied to our
high volume lines. Most of our IC's are available screened
to MlL-STD-883B, and our quality levels exceed the
most stringent military, TV and automotive
requirements.
Millions of Plessey complex function building block
IC's are being used in TV sets and car radios; CATV,
navigation and radar systems; frequency synthesizers
and telecommunications equipment.
Our global scope of operations, our high volume
manufacturing facilities, our proprietary processes ensure
that we will continue to deliver state-of-the-art technology
and reliability in IC devices at the appropriate prices and
in the required volumes. Day after day. Week after
week. Year after year.
•
Plessey Semiconductors
1641 Kaiser Avenue, Irvine, CA 92714. (714) 540·9979
9
Radar Signal Processing
minimum of external components (one
capacitor, one resistor per stage), yet has
a band-width of 500 MHz, a dynamic
range of 70dB and has a phase shift of
only ±3° over its entire range. As with
most of our other devices, it operates over
the full MIL-temp range and is available
screened to MIL-STD-883.
The chart summarizes our Radar Signal
Processing IC's. Whether you're working
with radar and ECM, weapons control or
navigation and guidance systems, our IC's
are a simpler, less expensive, more flexible alternative to whatever you're
using
now for any I.F. strip up to
I
160 MHz.
SL'~:"',~
For more details, please use the
postage-paid
reply card at the back
. .JOO~
_. '~, r~':""'_~N._~_..~.~.,!.!.~UT
of this book to order our RADAR
AND RADIO COMMUNICATIONS IC HANDBOOK, or
contact your nearest Plessey
Semiconductors representative .
.......
...._......._-_...__ .._..._
Since the perfonnance of a radar receiver
is critically dependent on the perfonnance
of its I.F. strip, we offer a range of "building block" IC's that can be used in systems
with different perfonnance requirements
and configurations.
The logarithmic I.F. strip shown is an
example of a low cost, high perfonnance
strip fabricated with Plessey IC's. It uses
only five devices and a single interstage
filter to achieve a logging range of 90 dB,
± 1 dB accuracy, - 90 dBm tangential
sensitivity and a video rise time of
LOW NOISE,
AGe.ABLE PREAMP
I
LOG I.F STRIP
S~L'SSO.~:.1S22
~
INI:UT~
-
-"
.
SL'S23_ . ' .
rT
SL~523
20 ns or less.
Three other Plessey IC's
complete the system simply
and economically. The AGCable SL1550 on the front end
improves noise figure, dynamic range and sensitivity.
The SL541 lets you vary video
output levels, with on-chip
compensation making it easy
to use. And the SL560 is a
"gain block" that replaces
your hybrid and discrete
amplifiers, usually with no
external components.
Another advanced system
function block is the Plessey
SL531 True Log Amplifier. A
6-stage log strip requires a
LOW NOISE BUFFER
AMP/LINE DRIVER
IF
PLESSEY IC'S FOR RADAR I.P'S
Wideband Amplifiers for Successive Detection Log Strips
SL521 30 to 60 MHz center frequency, 12 dB gain.
SL523 Dual SL521 (series).
SL1521 60 to 120 MHz center frequency, 12 dB gain.
S11522 Dual SL1521 (parallel).
S11523 Dual S11521 (series).
Low Phase Shift Amplifiers
True log I.F. amplifier, 10-200 MHz, ±0.5° /10 dB max
phase shift.
SL532 400 MHz bandwidth limiting amplifier, 10 phase shift
max. when overdriven 12 dB.
Linear Amplifiers
SL531
125 MHz bandwidth, 40 dB gain, 25 dB swept gain
control range, 1.8 dB noise figure, interfaces to
microwave mixers.
S11550 320 MHz bandwidth version of SL550.
SL560 300 MHz bandwidth, 10 to 40 dB gain, 1.8 dB noise
.
figure drives 50 ohm loads, low power consumption.
Video Amplifiers and Detectors
SL550
SL510
SL511
SL541
10
Detector (DC to 100 MHz) and video amplifier (DC to
24 MHz) may be used separately, 11 dB incremental
gain 28 dB dynamic range.
Similar to SL510 with DC to 14 MHz video amplifier,
16 dB incremental gain.
High speed op amp configuration, 175 V//lS slew
rate 50 ns settling time, stable 70 dB gain, 50 ns
recovery from overload.
Radio Communications
Our comprehensive line of radio system
function blocks is cutting costs, increasing
reliability and reducing the size of systems
I.
",
u
,
I
L
GrKii~ ~ -M!XER-
,
IF
• - - • FILTER'
,J, DECOlru,;J;- ,;J;'"
I
00:!Xru iOEcCUPt.f ' SoUElcH NllJSr- - - .J
,;J;-
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in applications that range from
commercial communications
to military manpack radios.
Using our bipolar Process I,
the Plessey SL600 Series
(hermetic) and SL1600 Series
(plastic DIP) feature a high
degree of integration, low
power consumption and exceptional system design flexibility for I.F:s up to 10.7 MHz.
Our SL6000 Series uses our
bipolar Process III to extend
our building block concept
even further. Devices all feature advanced circuit design
techniques that permit higher
levels of integration, lower
power consumption and
exceptional performance.
Typical is our SL6600, a
monolithic IC that contains a
complete IF amplifier, detector, phase locked loop and
squelch control. Power consumption is a meager 1.5 rnA
at 6 V, SIN ratio is 50 dB,
dynamic range is 120 dB and
THD is just 1.3% for 5 kHz
'.';;;
_
peak deviation. The SL6600 can be used
at I.F. frequencies up to 50 MHz, with
deviations up to 10 kHz.
If any of the Plessey devices appear interesting, use the postage·
paid reply card at the back of this
book to order our RADAR AND
RADIO COMMUNICATIONS IC
HANDBOOK. The Handbook includes full details on our integrated
circuits, along with a number of applications circuits and design tips
that will help you get the maximum
0U11'UT
system benefits from Plessey
products.
Or if your need is more urgent,
contact your nearest Plessey Semiconductors representative.
SQUELCH
PlESSEY RADIO Ie's
Amplifiers
SL610
SL611
SL612
SL613
SL1610 140 MHz bandwidth, 20 dB gain, 50 dB AGe
range, low 4 dB N.F., low distortion.
SL1611 100 MHz bandwidth, 26 dB gain, sim. to SL61O.
SL1612 15 MHz bandwidth, 34 dB gain, 70 dB AGe
range, 20 mW power consumption.
145 MHz bandwidth, 12 dB gain, limiting
amp/detector.
Mixers
SL640 SL1640 Double balanced modulator eliminates diode
rings up to 75 MHz, standby power 75 mWtypical.
Detectors and AGe Generators
SL620
SL1620 AGe with VOGAD (Voice Operated Gain
Adjusting Device).
SL621 SL1621 AGe from detected audio.
SL623 SL1623 AM SSB detector and AGC from carrier.
SL1625 AM detector and AGC from carrier.
SL624
AM/FM/SSB/CW detector with audio amplifier.
Audio Amplifiers
SL622
Microphone amp. with VOGAD and sidetone amp.
SL630 SL1630 250 mW microphone/headphone amplifier.
I.F. Amplifiers/Detectors
SL6600
FM double conversions with PLL detector.
SL6640
FM single conversion, audio stage (10.7 MHz).
SL6650
FM single conversion (10.7 MHz).
SL6690
FM single conversion, low power for pagers
(455 kHz).
SL6700
AM double conversion.
Audio Amplifiers
SL6270
Microphone amplifier with AGe.
Sl6290 SL6270 with speech clipper, buffer and relay driver.
Sl6310
Switchable audio amplifier (400 mW/9V/8 ohms).
Sl6440
High·level mixer.
11
R.EHybrids
To enhance your systems even further, we have established an R.F. hybrid manufacturing facility in our Irvine,
California, U.S.A. headquarters.
For small production quantities or extremely complex
functions, our hybrid capabilities can save you time and
money while improving your system performance, reducing system size and increasing system reliability. We
can help with your I.F. strips, instrumentation front ends,
synthesizer subsystems, high speed A-to-D and D-to-A
converters and other complex high-frequency functions.
They can be fabricated to MIL-STD-883 using thick
and thin film techniques, using our own integrated circuits in combination with discrete transistors, diodes and
other components.
Our IC functions represent the state-of-the-art in high
frequency integration, with ft's as high as 5 GHz. The
chips are backed by an in-depth in-house systems knowledge that encompasses radar, radio communications, telecommunications analog and digital conversion, frequency
synthesis and a broad range of applications experience.
We can work to your prints, or we can design a full system based on your "black box" specifications. For more
information, please contact: Plessey Semiconductors,
1641 Kaiser Avenue, Irvine CA 92714, (714) 540-9979.
12
13
Frequency Synthesis
Plessey's IC's offer a quick and easy way to lower
synthesizer costs while increasing loop response and
channel spacing all the way from dc through the HF,
VHF, UHF, TACAN and satellite communications bands.
Our single-modulus prescalers operate at frequencies
all the way up to 1.8 GHz. They feature self-biasing clock
inputs, TTL/CMOS-compatibility and all guaranteed to
operate to at least the frequencies shown, most of them
over the temperature range from -55°C to + 125°C.
Our 2-modulus and 4-modulus dividers expand your
system flexibility and allow even tighter channel spacing.
All of them provide low power consumption, low propagation delay and ECL-compatibility.
To simplify your systems even further, we also offer
highly integrated control chips. Our N]8811, for example,
includes a crystal oscillator maintaining circuit, a programmable reference divider, a programmable divider to
control the four-modulus prescaler and a high performance
phase/frequency comparator so that you can phase lock
your synthesizer to a crystal with none of the usual headaches and hassles.
We've put together a FREQUENCY SYNTHESIZER
IC HANDBOOK that details all of the Plessey IC's and
includes a number of applications circuits, practical
examples of how Plessey integrated circuits can simplify
your designs and improve system performance.
For your copy of the Handbook, please use the postagepaid reply card at the back of this book, or contact your
nearest Plessey Semiconductors representative.
Reference
Oscillator
Charge
Pump &
Phase
Comparator Filter
~
NP
Program Inputs
14
Frequency (MHz)
o
100 200 300 400 500 600 700 800 900 1000 1100 12001300 1400 1500 1600 17001800
,
"
,
" !
I
! ,
"
"
==IIIIIIIIIIIIIIIIUIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIII.
+2
[
111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111
111111111111111111111111111111111111111111111111111111111111111111111111111111111111111.
-
=lln1mllllulUlUlIlllI1II1I1II1I11IlIIUIlIUIlfIIllIllIlIlIllIIllIlIllIlIlUlIllIlIlIllIllIIllIlIlIUIIIIIIIIIIUIIIIIWIllIllIUIIIIlIIlIlIlIlIllIlIUIIlIlIIU
1111111111111"'"111111111111111111
-:-4
[
1111111111111111111111
fIllIlIlIlIlIlIllIllIlIlUlllllllttlIIIIUUlIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIWIIIIIIUllIlIlIlIIlllnlllllllm",IIll1JJmUlUllllllllllllllllllUlllllltllllllllllllilllllltllllllllllllllllllllllllUlIlIl1
1111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111IIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIIHIIIIIIIIIIIIIIIIIII11111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111
+5 [
1lIIIII11IIIImilUlllllllllllUIII111IUIIlIIIIHmlili •
111111111111111111111l11rllllmllluummUllUuumllllllllllllUlIUIIIIIIIIIIII.
+8 [
11111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111
1111111111111111111111111111111111111111111111111111111111111111111111111111111111111111
Illrrrrllllrrrrrl/tllllllllllllllllllllllllllllllllll.lIllllllllll11111111111111111111.
+ 10 [
111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111
111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111111I1111111111111111111111111111111111111111Ullllllllllllllllilltllllllllllll11
';'16 [
.;.20[
.;-24 [
1I111111111tlllllllllllllltlllllllllllllllllllllllllllllllllllllIJllllUWllllmlll1l1 •
11111111111111111111111111111
11111111111111111111111111111
Low Power
Frequency
_Power
IJJJJJUJlJIIIIIIIIIIIIII
11111111111111111111111111111111111111111111111111,*
+10/11 [
• -55e to +125C
2- Modulus
Dividers
:::::::::::::::::::::::::::::II:llIlIIllIlIIlUlllltlilltlilltlilltllltt.
=llIIlIllllIltlllIlllIlll1l11l1lll1l1ll11l11l1llll1llllll1l1ll1lll.
-:-20/22 [
IIl11l1l1tl1lllllllll1ll1ll1llll1l1l1llll1ll1ll1l1lll1l1l1mtllllllllUlrrrrrtllltllfllllUU1II11111111111111111111111111111111111111111111111111WlllllllltlilIJIIII
.;.40/41 [ ~1I1111111111111"' •
.;-80/81 [ :':'=:11111111111111111'.
7256/255/240/239 [
11I11I11I1I1111t1II1IIIII1I11I1I1IIIH1I1I1IIII1II1I1III1IIII1I1I11I11I11
.;- 512/511/496/495 [
'"III1I1IUUW)J1J11l1lmHIllIlIlIIIIIlInIlIII1lI1II1I1IIIIIIIIIIIIIII1I11I11I1III11I11111tlllllllllllllllllllllllll111tlllllLIIIIIII1IIIII1
o
50
100
150 200 250 300
350 400
450 500
]
4- Modulus
Dividers
550 600
Typical Power (mW)
15
Telecommunications
devices that plug directly into your
Plessey functional building block IC's
are exceptionally versatile. Designed
designs, we have a number of devices
from a systems standpoint, they redesigned for your low noise and ultraduce complexity and lower costs while
high frequency applications.
increasing the perfonnance of telecomThe Plessey TELECOMMUNICAmunications systems.
TIONS IC HANDBOOK contains complete
infonnation on all of these devices, as
Our SL600 Modulator/Phase Locked
well as application notes, to help you get
Loops are used in wavefonn generators
and in AM, PAM, FM, FSK, PSK, PWM, the most out of them. To get your copy,
please use the postage-paid reply card
tone burst and Delta modulators.
at the back of this book or call your nearest
Our S11000 Series amplifiers meet
the most stringent demands of telephone. Plessey Semiconductors representative.
transmission equipment.
Our transistor arrays with
up to five electrically and
Telecommunications Devices
thennally matched transistors
MJl440 HDB3 encoder/decoder
on a chip are ideal for disMJ 1444 PCM synchronizing word generator
MJ 1445 PCM synchronizing word receiver
crete and hybrid amplifiers
MJl471 HDB3/AMI encoder/decoder
and mixers. In addition to
Data Communications MOS
standard second-source
MP3812 32 x 8·bit FIFO memory, serial or parallel, up to
0.25 MHz data rates, easily stacked.
MJ2841 64 x 4-bit FIFO memory, 5 MHz clock rate.
Modulator/Phase locked loops
Sl650
Modulator/Pll for AM, PAM, SCAM, FM, FSK,
PSK, tone-burst and Delta modulation;
VFO variable 100:l.
Sl651
Similar to Sl650 without auxiliary amplifier.
Sl652
Similar to Sl650, low cost.
Telephone Circuits
SlIOOl Modulator/demodulator, 50 dB carrier and signal
suppression, -112 dBm noise level.
SlI021 3 MHz channel amplifier, stable remote
gain control.
SlI025 FDM balanced modulator, 50 dB carrier and signal
suppression, 5 dB conversion gain.
SlI030 200 MHz wideband amplifier, programmable gain,
low noise.
Transistor Arrays
PlESSEY
2ND-SOURCE
PlESSEY
2ND-SOURCE
PART NO.
PART NO.
PART NO.
PART NO.
Sl3081
CA3081
Sl3051
CA3951
Sl3082
CA3082
Sl355
NONE
Sl3083
CA3083
TBA673
TBA673
SL3183
CA3183
S1I495
CA1495L
Sl3146
CA3146
S1I496
MC1496G
Sl3093
CA3093
S1I496
MC1496l
CA3018
S1I595
MC1595l
Sl3018
Sl3018A
CA3018A
SL1596
MC1596G
Sl3118A
CA3118A
S1I596
MC1596l
Sl3118
CA3118
Sl3054
CA3054
Sl3050
CA3050
SL3086
CA3086
High frequency matched pair, ft=2.5 GHz.
Sl360
low noise matched pair, ft=2.2 GHz.
Sl363
Sl2363/4 5GHz dual long-tailed pair.
Sl3145
Five transistor array, ft=2.5 GHz.
16
Television Ie's
Plessey integrated circuits are in millions of homes, in television sets around
the world.
Economical and reliable, our devices
cover the range from remote controls
to touch tuners to frequency synthesizers,
as well as a range of second-source
devices for the IF color processing and
line oscillators.
For the 1980's, we have introduced the
Plessey KEY System, designed for maximum flexibility, simplicity and ease of
manufacture. The KEY System frequency
synthesizer offers accurate, high stability
frequency selection, channel and program
identification, and the very finest digital
fine tuning. It can be configured to
receive up to four completely different
standards (PAL, SECAM, SECAMF, and
NTSC) in a single TV set. It has 100 channel capability per standard, and includes
a 32-program non-volatile memory that
contains channel, fine tuning and standards /
information. And it can be interlaced to
a Plessey or other microprocessor for
games, Teletext or similar applications.
Complete data on all our television
devices has been assembled in our TELEVlSION IC HANDBOOK, along with
application notes to make them even
easier to use. Please use the postage-paid
reply card at the back of this book to order
your copy, or simply contact your nearest
Plessey Semiconductors representative.
SWlSO
SWlS3
SW170
CT2010
CT2012
CT2014
TDA2523
ALL TBA, TCA, lOA DEVICES ARE SECOND-SOURCED.
17
ECL III Logic and Data Conversion
As radar and communications systems
speed A-to-D converters. Our latching
become faster and more complex, the
SP9750 high speed comparator features
need arises for digital processing.
a maximum settling time of 2 ns, a propWe have developed a family of functions agation delay of 3.5 ns and is capable of
operating at rates up to 100 million
with speeds unequalled anywhere.
Part of our family is a range of ECL III samples per second.
Currently, our devices are being used
logic that is a direct plug-in replacement
for MECL logic, including low impedance in radar and video processing, nucleonics
as well as high impedance devices. We
systems, transient recorders and secure
extended the range by adding functions
speech transmission systems. We have
with lower delays and much higher operat- compiled a number of application notes
ing speeds. Our SP16F60, for example,
and details on the devices in our ECL III
is the world's fastest dual4-input
LOGIC AND DATA CONVERSION IC
OR/NOR gate, with a switching speed of HANDBOOK. To get your copy, please
use the postage-paid reply card at the
just 500 picoseconds. Devices can also
be selected for certain specifications
back of this book, or contact your nearest
(such as threshold voltage or slew rate on Plessey Semiconductors representative.
our SP1650/1, toggle rates
or delays on our SP1670) to
HIGH SPEED ECl III LOGIC
handle your most demanding
SP1648
Voltage controlled oscillator
applications. We've also
SP1650
Dual AID comparator, H i-Z
SP1651
Dual AID comparator, lo-Z
developed a family of high
SP1658
Voltage controlled multi vibrator
speed comparators and
SP1660
Dual 4-IIP OR/NOR gate, Hi-Z
SP1661
Dual 4-IIP OR/NOR gate, Lo-Z
circuits for ultra- high
SP1662
SP1663
SP1664
SP1665
SP1666
SP1667
SP1668
SP1669
SP1670
SP1671
SP1672
SP1673
SP1674
SP1675
SP1692
SP16F60
Quad 2-IIP NOR gate, Hi-Z
Quad 2-I/P NOR gate, lo-Z
Quad 2-IIP OR gate, Hi-Z
Quad 2-IIP OR gate, lo-Z
Dual clocked R-S Flip-Flop, Hi-Z
Dual clocked R-S Flip-Flop, lo-Z
Dual clock latch, Hi-Z
Dual clock latch, lo-Z
Master-slave D Flip-Flop, Hi-Z
Master-slave D Flip-Flop, Hi-Z
Triple 2-IIP exclusive-OR gate, Hi-Z
Triple 2-IIP exclusive-OR gate, lo-Z
Triple 2-IIP exclusive-NOR gate, Hi-Z
Triple 2-IIP exclusive-NOR gate, Lo-Z
Quad line receiver
Dual 4-IIP OR/NOR gate
HIGH SPEED DATA CONVERSION PRODUCTS
SP9680 High speed latched comparator_
SP9685 Ultra-fast comparator; 0_5 ns typical set-up time; typical
2_2 ns propagation delay; excellent CMR_
SP9687 Dual SP 9685.
SP9750 High speed latched comparator with precision current
source, wired-OR decoding; 2 ns min. set-up time; 2.5 ns
propagation delay.
SP9752 2-bit ADC expandable to 6-bit ADC; very fast 125 MHz clock.
SP9754 4-bit ADC expandable to 8-bit ADC; very fast 100 MHz clock.
SP9768 8-bit DAC; extremely fast; available 3rd quarter 1980.
SP9778 8-bit SAR; works with SP9768 to make a two-chip successive approximation ADC (20 MHz ciock); available 4th
quarter 1980.
18
MNOS Non-Volatile Logic
As semiconductors become more pervasive in military
and commercial applications, the need for non-volatile
data retention becomes more and more criticaL
Plessey NOVOL MNOS devices answer that need, and
will retain their data for at least a year (-40°Cto +70°C)
in the event of "power down" or a system crash.
Our devices all operate from standard MOS supplies
and are fully compatible with your TTL/CMOS designs.
The high voltages normally associated with electricallyalterable memories are generated on-chip to make
system interface simpler and less expensive.
Plessey NOVOL devices provide a reliable, sensible
alternative to CMOS with battery back-up or mechanical,
electro-mechanical and magnetic devices. Applications
include metering, security code storage, microprocessor
back-up, elapsed time indicators, counters, latching
relays and a variety of commercial, industrial and
military systems.
For more information, contact your nearest Plessey
Semiconductors representative, or use the postage-paid
reply card at the back of this brochure to order your copy
of the Plessey NOVOL literature package.
PlESSEY NOVOl MNOS
MN9102
MN9105
MN9106
MN9107
MN9108
MN9110
MN9210
*
4-bit Data latch ( + 5V, -12V)
4-Decade Up/Down Counter (+ 5V, -12V)
6-Decade Up Counter (12V only)
IOO-Hour Timer (12V only)
IO,OOO-Hour Timer (12V only)
6-Decade Up Counter with Carry (12V only)
64 x 4-Bit Memory
8 x 4-Bit Memory
6-Decade Up/Down Counter, BCD Output
6-Decade Up/Down Counter with Preset BCD Output
* COMING SOON
19
Power Control
Plessey power control devices are highly
integrated not just to solve the problems,
but to solve them at a lower cost than any
other available method.
For timing, our devices use a pulse
integration technique that eliminates the
need for expensive electrolytic capacitors,
thus increasing accuracy and repeatability
while reducing costs. An integral supply
voltage sensing circuit inhibits triac gate
drive circuitry if the supply is dangerously
low to prevent half-wave
firing and firing without
achieving complete bulk
conduction. A zero-voltage
Sl440
Proportional phase
control for motors, lamps
and lower power, fast
response heating.
Sl441
Similar to Sl440, with
proportional temperature
control and thermister
malfunction sensing, for
hairdryers, soldering
irons and food warmers.
spike filter prevents misfiring on noise
inputs. Symmetrical control prevents the
introduction of dc components onto the
power lines.
Devices have been tailored for
specific applications as indicated in the
chart. For more information, please use
the postage-paid reply card at the back of
this book to order our POWER CONTROL
IC HANDBOOK, or contact your nearest
Plessey Semiconductors representative.
LOAD CURRENT
11
SERVO
~~~~~
I
IINVERTlNG) I
I
Sl442
Sl443
Similar to Sl441 with
manual power control,
long timing periods for
hot plates, electric
blankets and traffic lights.
Sl444
Similar to Sl441 for 240V
permanent magnet motor
with thermal trip,
current limit detector.
Sl445
Proportional or On/Off
control, temperature trip/
inhibit circuitry, lED and
alarm drive facilities, for
ovens, heaters, industrial
temperature controllers.
Sl446
On/Off servo loop temper·
ature controller, lowexternal component count, for
water and panel heaters,
refrigerators, irons.
TBAI085
SERVO
AMPLIFIER
VARIABLE
OELAY
I
Switch mode power supply control, up to 40 kHz,
integral oscillator, variable ratio space/mark
pulses, soft'start, dynamic
current limiting, OVP.
I
I
L __ _
PULSE
GENERATOR
1l
SERVO ERROR
OUTPUT
..
~.:",.~~~':: • •
I
TIMING
CAPACITOR C1
SL440
I
',~~~~ ~,M:.'~~.~
'.
.:::: :::::::g.
"~-----1
".... 'r-----m.
Motor speed control
SL445
20
Processes,TestiIffi~ ~illlcdl QUIl21llnltyCC(())IDltrol
Just as we applied our systems knowledge
to the partitioning of functions to make our
IC's extremely flexible and cost effective,
we also developed an internal system concept to ensure that we could deliver our
state-of-the-art solutions year after year.
Our concept of standard processes
and rigid design rules ensures that our
devices are reproducible this year, next
year and five years from now. Our continuing investment in research and
development ensures that any new products we introduce will be on the leading
edge of technology, yet with the same
high performance and reliability that our
customers have come to expect as the
Plessey standard.
The result is that millions of Plessey
devices have been built into TV sets and
car radios; CATV, navigation and radar
systems; frequency synthesizers and
telecommunications equipment.
21
Plessey MOS Processes
P-channel metal gate MOS has been
in production for years and is used for
both standard Plessey products and custom LSI. Using ion implantation to modify
transistor and field threshold voltages, we
can reproduce virtually any p-channel
metal gate process, with or without deple·
tion loads.
MNOS (non-volatile) is essentially a
p-MOS process with variable threshold
memory transistors fabricated alongside
conventional MaS transistors. A modified
oxide-nitride gate dielectric permits the
injection and retention of charge to change
the threshold voltage. Current Plessey
products will retain an injected charge
for at least a year, and include an onchip high voltage generator so that
they may be used with standard
supply voltages.
N-channel metal gate MOS uses
an auto-registration co-planar process
with layout similar to our p. MOS. Ion
implantation is used to define the thres·
hold voltage of the depletion and enhance·
ment transistors. The constant·current·likE
characteristics of depletion load devices
give the most effective driving capability,
and enhancement· depletion technology
simplifies design and increases packing
density. The field threshold voltage is
also controlled by an ion implant, allowing
the use of a lightly doped substrate. This
reduces both the body constant and the
junction capacitance and results in faster
switching speeds.
METAL GATE MOS
I
High/Low Threshold
lIon Implantation
I I
I
Depletion/Enhancement
VT = 1.0 to 7.0 volts
Integrated MOS & MNOS
Vr(MOS)= -2 volts
/30 (MOS)=4 to 9/lAN'
Vr FIELD>60 volts
BVoss >60 volts
V;' =>20 volts
Vr(MNOS)=Electrically
/30=4)012 J1A/V'
alterable between 0 and
-16 volts typo
CUSTOM DESIGNS
MN9000 SERIES
22
I
r
V =18 volts
V'-r=7 volts
BVOSS=20 volts
BVoss=20 volts
~~"
IL
to
3O"AI'"
VT ENHANCEMENT= 1V±0.2
VJ DEPLETION= 1.8V±O.3V
CLOCK FREQ.=8 MHz
CUSTOM DESIGNS,
AUTOMOTIVE AND
MICROCELL
J
TELECOMMUNICATIONS
SYNTHESIZER CONTROLLERS
TV SYNTHESIZERS
Plessey Bipolar Processes
Bipolar Process I is a conventional
buried +N layer diffusion process with
f t =600 MHz and other characteristics
similar to industry-standard processes.
Applications range from high reliability
military devices to high volume consumer products.
Process Variant
Application
BVCBO@ 10IlA
BVEBO @lOIlA
LVCEO
VCE (SAT) @
IB=lmA,
IC=lOmA
hFE@ IC=SmA,
VCE=SV
IT @ IC=SmA,
VCE=SV
A
General
Purpose
20Vmin.
S.3V to
S.BSV
l2Vmin.
B
Non
Saturating
Logic
10Vmin.
S.lSVmin.
BVmin.
G
D
Saturating
Linear
Logic
Consumer
10Vmin. 4SVmin.
S.lSV min. 6.BV to
7,4V
BVmin.
20Vmin.
0,43V
max.
40 to 200
0.32V
max.
SO min.
0,43V
max.
SO min.
0.6V
max.
50 to 200
SOO
MHz
SOO
MHz min.
SOO
MHz min.
3S0
MHz min.
Bipolar High Voltage (HVI Process is
a variant of Process I that yields an LVceo
greater than 45 volts. Doping levels can
be controlled and an extra diffusion used
to fabricate a buried avalanche diode with
a 40 V breakdown for absorbing powerful
noise transients without being destroyed.
Process Variant
BVCBO @ 10llA
BVEBO@ 10llA
LVCEO
VCE/(SAT)@ IB=lmA,
IC=lOmA
hFE@ IC=SmA
VCE=SV,
IT @ IC=SmA, VCE=5V
CA
BOVmin.
7.2V to B.OV
4SVmin.
0.4V max.
BO to 300
250 MHz min.
Bipolar Process III uses very shallow
diffusion and extremely narrow spacing
for high frequency integrated circuits with
unusually low power consumption and
high packing densities. An f t of 2.5 GHz
allows us to routinely produce analog
amplifiers with bandwidths as high as
300 MHz and low power dividers and
prescalers that operate at frequencies up
to 1.2 GHz. Process variants allow us to
produce devices with an extended /3,
higher breakdown voltages and very
small geometries.
Process Variant
Application
BVCBO@ 10llA
BVEBO@ 10llA
LVCEO
VCE (SAT) @ IB=lmA,
IC=lOmA
hFE @ IC=5mA, VCE=2V
IT @ IC=5mA, VCE=2V
WE
Digital
10V min.
5.lV to S.BV
7Vmin.
O.SV max.
40 to 200
1.B GHz
Bipolar Process 3V is an f'xtension
of our Process m. Ion implantation and
washed emitters have given the process
an f t =6.5 GHz, allowing us to produce
dividers working at 2 GHz, logic gates
with delays of less than 500 picoseconds
and linear amplifiers at 1 GHz.
Process variant
Application
BVCBO @ 10llA
BVEBO @ 10llA
LVCEO@ SmA
VCE(SAT) @ IB=lmA,
IC=lOmA
hFE @ IC=lOmA, VCE=SV
fT @ IC=5mA, VCE=2V
wv
Digital
BVmin.
3.0Vto S.OV
6Vmin.
0.5Vmax.
40 to 120
6.5 GHz
23
Testing and Quality Control
A major thrust of our development
work is to ensure that our processes will
routinely produce reliable devices. Our
Process ill has a projected MTBF of
400,000 hours while our Process I is
even better.
Our facilities include the latest test
equipment (such as the Macrodata MD501,
Teradyne J324 and Fairchild Sentry VII
and Sentinel) to allow us to perform all the
necessary functional and parametric testing in-house. We have an internal capability
to provide specific applications-oriented
screening, and most Plessey IC's are available screened to MIL-STD-883 and other
international specifications. Our quality
levels exceed the most stringent military,
TV and automotive requirements as a
matter of course.
But the best proof of all these claims
is our products themselves. After you've
reviewed the products that could help you
with your systems, use the postage-paid
reply card or contact your nearest Plessey
representative for complete details.
ASSEMBLY OF INTEGRATED CIRCUITS
QUALITY ASSURANCE
o
D
<>
24
KEY
PROCESS OPERATION
IN-LINE INSPECTION
MONITOR OR QUALITY
CHECK
I.C. Screening to MIL-STD-S83
The following Screening Procedures are available from Plessey Semiconductors
class
A
class
B
class
C
*standard
products
PRE CAP
VISUAL
PRE CAP
VISUAL
PRE CAP
VISUAL
PRE CAP
VISUAL
STABILIZATION
BAKE
STABILIZATION
BAKE
THERMAL
SHOCK
TEMPERATURE
CYCLING
MECHANICAL
SHOCK
CENTRIFUGE
CENTRIFUGE
HERMETICITY
HERMETICITY
INTERIM
ELECTRICAL TEST
INTERIM
ELECTRICAL TEST
BURN-IN
BURN-IN
HERMETICITY
HERMETICITY
FINAL
ELECTRICAL TEST
FINAL
ELECTRICAL TEST
INTERIM
ELECTRICAL TEST
REVERSE BIAS
BURN-IN
FINAL
ELECTRICAL TEST
Plessey Semiconductors reserve the right to change the
Screening Procedure for Standard Products.
25
26
2. TV FREQUENCY
SYNTHESISER
27
28
INTRODUCTION
The Key System is a second-generation frequency synthesis kit of integrated circuits, developed by Plessey Semiconductors for the television market. The first generation system (which
many other manufacturers have since attempted
to emulate) prompted suggestions from customers for other features that they would like to
see incorporated into such a system_ This valuable input, combined with Plessey Semiconductors' expertise in frequency synthesis and
high speed dividers, led to the design of the Key
System.
The Key System is not simply a re-vamp of the
first-generation kit, but rather a complete redesign. The aim was to simplify the television
designer's task by offering circuits which could
be grouped together in cost-effective modular
blocks. By choosing an appropriate selection
from the wide range of options available within
the Key System, the designer can quickly assemble a configuration which is tailored to his
specific requirements.
Fig.l shows, in simplified form, the essential
elements of the Key System.
FEATURES
tELETEXTlVlEWDATA
BLOCK
programmed with tuning information for the most
common PAL, SECAM and NTSC standards.
To allow expansion to higher levels of sophistication, Plessey Semiconductors have developed
a range of optional circuits for the Features
Block. These circuits (again, controlled via the
Keybus) at present provide digital clock, onscreen display, and a Keybus-Mibus interface for
Teletext and Viewdata.
In Keyway 1, the component ICs of the Key
System are described, and a number of configurations illustrated. In addition, the general principles of frequency synthesis are discussed in
Appendix 1 and a summary of Key System
circuits is given in Appendix 2.
THE SYNTHESISER BLOCK
Fig.2 shows the Synthesiser Block, comprising
the CT2010, CT2012 and CT2017. Together
with the varicap-controlled VCO in the tuner,
they form a phase-locked loop which is controlled
via the Keybus. The CT2010 includes a sensitive
pres caler which requires no additional pre.
amplification of the tuner's local oscillator signal.
Radiation from the circuits in the Synthesiser
Block is very low: screening round these circuits
is, therefore, not necessary.
The Synthesiser Block contributes the.following
features:
•
-;- 20 prescaler(CT201O)
•
-;-19/20 two-modulus divider (CT2010)
•
Delay-tolerant modulus control
•
2.5kHz reference frequency (CT2012)
•
Power low detector (CT2017)
•
Signal quality detector (CT2017)
•
Varicap control (CT2017)
•
'Exact' tuning in 50kHz fine tuning steps
Full technical data for the CT2010, CT2012
and CT2017 are published in Keydata,
Synthesiser Block.
(OPTIONS)
ON·SCREEN
DISPLAY
Fig. 1 The Key System
The Synthesiser Block (comprising three integrated circuits which are common to all Key
System configurations) provides highly accurate
phase-locked loop tuning and is used in
conjunction with a conventional varicap tuner.
The Synthesiser Block is controlled by means of
coded information transmitted on the Keybus
data highway by the Control Block.
Just as the Syn thesiser Block con tribu tes precision and stability of tuning, so the Control Block
provides the versatility of the Key System through
the wide range of optional circuits and configurations available. Control Block options include
local and remote programme selection, dedicated control ICs, microprocessor control and a
selection of four read-only memory 'Key' circuits
Fig. 2 Synthesiser Block
KEYBUS
The Keybus is a four-line bi-directional data
plus multiplex clock highway. Control codes are
29
sent along the Keybus when the clock is low, and
data when clock is high. Ones or zeroes are
inserted between adjacent codes or data words to
avoid spurious instructions. All devices driving
the Keybus should have open drain outputs, for
which pull-up resistors (nominally 4kQ) are
included in the CT2012.
CONTROL BLOCK
The integrated circuits from which a variety of
Control Block configurations can be constructed
include: three Control circuits CT2014, CT2015
or CTl650A/PIC1650Z-20 microprocessor; a
choice of up to four CT2030 series Key ROMs
{each programmed with 100 channels of stored
frequency and name informa tion and the ML 1900
and ML 191 0 remote control receiver/transmitter
combina tion.
Also optional to the Key System Control Block
is the ER1400/NC7400 non-volatile memory,
which can be used to store (against each programme number) Key location, channel number
(channel name and band accessed from Key),
fine tuning adjustments and Auto on/off
information.
An alternative to the use of any of the above
Control circuit options is a Control Block consisting of a microprocessor chosen and programmed by the system designer. This choice
still enables the benefits of the Plessey Key
System Synthesiser Block to be reaped, while
using the microprocessor to perform other func·
tions as well as controlling the phase-locked loop.
Key Circuits (CT2030 series)
The emphasis throughout the Key System is
high technical performance and flexibility at a
competitive price. For this reason we have designed the Key circuits, each one of which contains a 100 channel ROM to tune to the correct
channel frequencies for a particular IF. Hence,
each Key is designed for one particular standard.
Obviously, since we have gone to the trouble of
giving the possibility of 'exact' tuning (by using
50kHz fine tuning steps in the PLL), it makes
sense to use the exact frequency rather than an
approximation based on another transmission
standard's IF. Up to four Key circuits can be
attached to the Keybus, giving the opportunity
for a multistandard system.
In addition to holding the frequency list for one
particular standard, information is also stored in
each Key circuit for the channel name and band
against each channel number. The necessary
interface logic for the non-volatile programme
memory is also present on each Key circuit. Since
these devices are pin compatible with each other,
their position on the Keybus is immaterial, any
Key can occupy the prime (Key 0) position
through which any other Keys will interface with
the programme memory.
The CT1650A/PIC1650Z-20 does not require
an external Key circuit to be added to the bus.
Information from one Key, the CT2030 (Pal B &
G) has been included in the memory of this micro·
processor.
The Non-Volatile Programme
Memory
An optional add-on to every Control Block is a
non-volatile programme memory. We have used
30
the well-proven 14 x 100 ER1400INC7400
which is available from a number of suppliers.
This is capable of storing the following
information for each of 32 programmes: Key location, channel number, fine tuning information
(50kHz steps), Auto Mode bit. The Key location
information is not stored in the single-standard
microprocessor version.
On selection of a programme number, the nonvolatile memory is read to give the Key location;
this will access the appropriate division ratio
stored against the channel number in the
relevant Key. The correction tuning information
is also fed out of the programme memory and, if
the Auto bit is set, the system will switch to Auto
Mode. In this mode of operation the digital
signals from the CT2017 AFC Control are sent to
the control circuit (CT2014, CT2015 or
CT1650A, etc.) where they are used to change
the frequency in the PLL in 50kHz steps. If the
correction tuning is changed manually, the Auto
Mode bit will be cancelled. Therefore, in order to
store both correction tuning data and set the
Auto Mode bit, the correction tuning must be
stored first.
CT2200 Display Driver
If one wishes to show the programme selected
on LED displays, then the CT2200 nonmultiplexed display driver can be used in conjunction with two seven-segment, common-anode
arrays.
This device takes the 5-bit binary input, 00000
to 11111, and directly drives two displays, 1 to
32. The only external components needed are for
brightness control (as illustrated in Fig .3). The
CT2200 is driven from the + 5 V supply used
throughout the system.
MLl900/10 Remote Control
The Remote control circuits, the ML1910
receiver and the MLl900 transmitter offer the
following fea tures:
•
Up to 288 commands (including Teletext,
Viewdata, etc.)
•
'Base Mode' plus eight shift modes
•
Six analogues, 64 levels
•
MLl910 receiver doubles as 'local'
keyboard encoder
•
Full compatibility with CT2015 and
ML2000 series (see Features Block, below)
FEATURES BLOCK
It may be that the designer would like to add to
his system some special feature which can be
activated from local or remote control. Our
ML2000 series is designed to work with the
ML 1900 series to meet just such a requirement,
allowing the manufacturer to add that individual
touch to his product range. We will be happy to
discuss this type of development. These special
Features circuits are designed to be controlled
externally from the Keybus with the minimum of
external components.
Circuits already in development are:
•
ML2001 Keybus/Mibus interface for teletext
and viewdata
•
ML2020 12 or 24 hour crystal clock (LED
and/or on-screen display)
•
ML2040 On-screen display (includes
channel name, e.g. S14)
SYSTEM CONFIGURATIONS
A Basic CT2014 System
A system giving local or remote selection of up
to 32 programmes is shown in Fig .3. Channel
information is stored in the non-volatile memory
by a 14 line digital input. This configuration is
well suited to the rental market.
Many viewers, once their television set has
been 'tuned' to certain stations, prefer to select
just programme numbers. The configuration
shown in Fig.3 allows the programme memory to
be set up by using switches (as shown in Fig.4) to
enter details of transmission standard, channel
number, fine tuning and the signal tracking
option (Auto). Of course, since the Key System
uses frequency synthesis, the sta lions required do
not have to be transmitting in order to initialise
the programme memory. Having programmed
the memory, if access to the switches is prohibited, this tuning information is fixed in the
non-volatile programme store. Thus, accidental
off-tuning of the set is not possible. Access to the
fine tune and Auto switches allows re-tuning
limited to the correct channel only.
If only one Key is used then the switches for
KEY SELECT are not required. The particular
Key chosen, depends on the market region being
served.
To fill a memory location, first the particular
programme number is selected, then the
appropriate Key and the desired channel number
are set up on the switches. Closing the TUNE
switch causes the Key and channel number to be
written in the selected memory location. In most
cases, this will be all that is required. However, if
___-;.---4
KEY SElECTCSTAHOAAD)
-==::t==i} ON"." ".""OJ
Fig. 4 Switches to initialise the programme memory
for any reason the transmitted signal is not
exactly in the centre of the channel, then the
system can be tuned to an off-centre frequency by
using the manual fine tune switches. These
enable a tuning correction to be stored in the
memory location in 50kHz steps from -3.9MHz
to + 4MHz of the channel centre.
These switches have immediate effect on the
picture and programme memory. They operate
with roll over at end of channel, so it is impossible
to tune outside the desired channel.
If the transmitted signal is likely to drift, the
Auto bit may be set in the memory location. This
will activate the Auto Mode, fine tuning the
system using AFC (whilst remaining in the phaselocked loop), every time that particular programme is chosen.
Programme selection can be either by local or
remote control; the input used is five bit binary.
Fig. 3 A single-standard CT20 14-con trol/ed system
31
Multistandard CT2014 control
The Control Block in Fig.S is similar to the one
in Fig.3, the difference being that the user is
allowed local control of channel and fine tuning.
Up to 32 programmes can be selected from local
or remote control. Fine tuning can also be controlled remotely with the addition of some logic.
Fig.S shows how the basic system, already described, can be expanded. The method of
initialising the programme memory is as before
but, in this case, the viewer may be allowed to
directly change Key (standard), channel or fine
tuning information allocated to a programme
number.
Up to four Keys can be added to the Keybus,
giving a multistandard system. This option is also
available with CT20 IS control.
The method by which the Key and channel tens
and units are selected is optional. Either BCD
switches, or a running counter can be used.
However, single pole switches may be preferable
if the user is not allowed access to these switches.
If the viewer is permitted to select a station by
channel number then one or several memory
locations can be allocated for such use. The new
channel information can only be tuned to and
stored in the memory when TUNE is enabled. If a
STORE command is required instead of automatic programme update, then a CT201S configuration should be used (see Figs.7 and 8). If no
programme store is required then, as in all Key
System configurations the non-volatile programme memory may be omitted.
The channel number and fine tuning .information stored in the memory can be accessed via the
Control circuit by the S bit programme number.
This input is well suited to remote control
interfaces. The CT2200 is again used to display
the selected programme number whilst a 7447 is
used to display the Key and channel numbers
chosen.
As already indicated, it may be desirable to
place the switches for Key and channel number
away from the front of the set. The TUNE button is
required to update this information, so it too may
be concealed for the purposes of everyday operation of the receiver. The FINE. TUNE UP, FINE
TUNE DOWN and AUTO push button switches
do not affect the channel number accessed,
therefore they may be left on the control panel of
the set. Both fine tune switches operate with 'roll
over' within the 8MHz channel as does the AUTO
switch. If a viewer has difficulty returning to a
signal which he has tuned away from, he can return by keeping one of the fine tune switches depressed or by simply pressing the AUTO button.
Any fine tune adjustments and the AUTO
command are automatically stored in the nonvolatile memory against that programme
number.
Fig. 5 A multistandard CT2014·control/ed system
32
Microprocessor control
We have already indicated that the Synthesiser
Block (CT201O, CT2012 and CT2017) is very
well suited to a microprocessor application, an
example of which is shown in Fig.6.
The Control Block is connected to the Synthesiser Block via the Keybus as before. One Key is
programmed into the microprocessor (CT1650AI
PIC1650Z-20). Features available are manual
and auto fine tuning, channel and programme
selection, plus a channel sweep. Remote control
can be expanded from programme selection to
operating the other features.
The CT2014 provides several configurations
which are ideal for the European Market or others
where station selection is by programme number.
The CT1650A/PIC1650Z-20 gives a little more,
for markets where sometimes channel numbers
are used for tuning by the viewer, but usually all
that is required from remote control is programme selection. As well as local or remote control of up to 32 programmes, push-button
local controls allow channel selection, channel
sweep, fine tuning, AUTO selection and programme step. This version fills the gap between
the simple and comprehensive frequency synthesis systems.
It will be observed that no Key circuit is
present in this application. This is because the
CT1650A/PIC160Z-20 has an internal 'key',
for PAL Band G.
To initialise the programme memory, first
select the required location then the channel
number (by Channel Tens Step and Channel
Units Step). If the station is off-centre then any
necessary fine tuning performed is also automatically stored. Similarly if AUTO MODE is
selected, the AUTO bit is set for that programme.
Again, because of the automatic programme
information update feature in this system, it is
recommended that either the programme
memory is disconnected or a special location is
allocated for temporary channel tuning.
+5V
+12V
Fig. 6 A microprocessor·controlled system
33
Multistandard CT2015 system
The configuration of the Control Block shown in
Fig.7 allows full control of all features,
which are: direct channel and programme selection, manual and auto fine tuning, sweep, store,
channel tens and units stepping, programme
stepping, and selection of up to 4 standards (by
using the Key circuits).
The CT2015 control also allows other devices
to be added to the Keybus, for example, clock,
TeletextNiewdata interface and on-screen
display.
The CT2015 control circuit gives the manufacturer the ability to configure his own system,
which in terms of features and performance leads
the market. It is the most versatile of the Key
System control options.
The CT2015 interfaces, through the Keybus,
.5.
with the ML191O-a remot~ control receiver
which doubles as a keyboard encoder. The
ML 1900 remote control series is briefly described
later in this edition of Keyway and, together with
the ML2001 (KEYBUSIMIBUS interface), more
fully in Keyway 5.
The features offered with the configuration
shown in Fig.7 are: direct channel and 'programme selection, channel and programme stepping, channel sweep, store command, manual
and Auto fine tuning (again, 50kHz step), control
of a teletext decoder, control 01 a clock, six analogues, 32 programmes, storing fine tuning
adjustments and 'Switch to Auto' command,
choice of up to four transmission standards, and
standard, channel and programme number
displays.
CER1~~
Fig. 7 A multistandard CT2015·controlled system
34
___--l+'2V
Single Standard CT2015 system, with
full remote control
The system configuration of Fig.8 shows how
the system illustrated in Fig.7 can be converted
to full remote control. The CT2200 and 7447 display drivers have been replaced by the ML2040,
which of course could have been used in the
previous system. The Key circuit could be any
one of the CT2030 series. The choice depends on
the market which the system is designed for.
More Keys could be used if a multistandard
system were to be required.
The logic that controls the Keybus in the
CT2015 enables other Features Block circuits to
be added to the Keybus, for example, the
ML2020 clock circuit. By 'polling' round the devices, the CT2015 allocates use of the Keybus to
such circuits in turn, according to a priority setting in each Features circuit.
The features offered with this configuration
are: direct channel and programme selection,
channel and programme stepping, channel
sweep, store command, manual and Auto fine
tuning (again 50kHz step) six analogues, 32 programmes, storing fine tuning adjustments and
'switch to Auto' command, choice of up to four
transmission standards, and standard, channel
and programme number on-screen displays.
All of the tuning features available in the configuration of Fig.7 are also present in this system,
with the addition of the remote control facility.
The local and remote keyboards can be identical
as each is capable of initiating the full 288
command instruction set which is possible with
the MLl900 series.
A possible Keyboard with transmitter codes (F
is MSB) is shown in Fig.9.
+5V
50kHz
ML1910
REMOTE CONTROL RECEIVER
AND KEYBOARD ENCODER
Fig. 8 A CT2015·controlled system incorporating full remote control
35
FED
,
110
101
100
011
010
TIME
,'STANDARD
AUTO
FINE
TUNE
UP
FINE
TUNE
DOWN
G
ON/OFF
&.
SHIFT
III
SHIFT
&.
SHIFT
+
ANALOGUE
6
G
B
(2)
B
(2)
0
PROGRAMME
STEP
'TMD.P.OFF
UP
*
NORMALISE
ANALOGUE
6
pROGRAMME
STEP
DOWN
:sz
t::.,.
0
0
0
0
0
(0
0)
..
'TMD.P.ON
O.
STANDBY
MUTE
~
+
+
+
+
+
ANALOGUE
ANALOGUE
ANALOGUE
ANALOGUE
5
4
2
ANALOGUE
3
1
-
-
-
-
ANALOGUE
ANALOGUE
-
5
ANALOGUE
ANALOGUE
ANALOGUE
4
3
2
1
001
'INCA DAY
'CH.SWEEP
'REVEAL
'REVEAL
'INCR HRS
'CH.T.STEP
000
(111000)
CBA
000
,
'FULL PAGE
'FULL PAGE
'INCRMINS
'CH.U.STEP
'2xhtTOP
'2xhtTOP
'STARTCLK
'STORE
'2xhtBTIM
'
'TAPEWRT
"2xhtSTIM
'RING OFF
001
,
,
,
010
'TAPE READ
,
lHOLD
011
,
3UPDATE
lMIX
'UPDATE
'MIX
A
SET TIME
SHIFT
&.
TUNING
SHIFT
RECALL
101
&.
TELETEXT
SHIFT
&.
VIEWDATA
SHIFT
\l
&.
SHIFT
Fig. 9 A possible keyboard with transmitter codes
Summary
The Synthesiser Block (CT2010/l2/17) contributes the following features:
• 'Exact' tuning in 50kHz fine tuning steps
• Delay-tolerant modulus control
• Sensitive pres caler
• Power-low detector
• No extra screening required
• Signal quality detector
Key circuits (CT2030 series) give:
• I standard per "Key"
• 100 channels per "Key"
-required division ratio
-channel name
-band
Control Circuit options
The facilities available with the various control
circuit options are as follows:
CT2014
•
•
•
•
Choice of single or multistandard system
Remote control programme selection option
Limited use of Features Block circuits
Direct channel and standard selection (BCD
input)
CT201S
•
•
•
•
•
•
•
•
•
•
Choice of single or multistandard system
Remote control selection option
.
Full use of Fea tures Block circuits
Direct channel selection
Direct programme selection
Store command
Channel sweep
Channel tens/units step
Programme step up/down
Keybus control logic
CT16S0A/PIC16S0Z-20
•
•
•
•
•
•
36
Single standard microprocessor system
Direct channel selection (tens and units
steps)
Programme number step
Channel sweep
Remote control selection option
Limited use of Features B~ock circuits
APPENDIX 1
/
THE KEY SYSTEM - FREQUENCY SYNTHESIS FOR TELEVISION
The Basic Loop
The Plessey Key Frequency Synthesis System is based on the principle of the phase
locked loop (PLL). A basic PLL is shown in Fig. 1. In this case the output, fo, from the
voltage controlled oscillator is divided by a number, N, to give a convenient comparison frequency, fe. The other input for comparison is the reference frequency, ff<
derived from a frequency standard.
Fig. 1 Basic phase·/ocked loop
The phase comparator produces a voltage which is fed back via a filter to the voltage controlled oscillator. This feedback loop enables the local oscillator frequency, L,
to be phase locked to the reference frequency, fro Thus:
and when phase lock occurs, fe
fo = N.fe
=
fro so
fo = N.fr - - - - - - - - - - (l)
By choosing an appropriate reference frequency, ff< and a suitable divider whole
number N, we can now synthesise a series of frequencies, fo, in steps of fro However,
such a basic loop gives a very limited range of frequencies.
A Simple System
A simple practical system is shown in Fig.2. In this case, an output from the varicap
controlled local oscillator is divided down by a fixed prescaler of division ratio, A,
and a programmable divider of division ratio, N, to a convenient comparison frequency, fe. An accurate stable frequency, t is established by dividing down the
output of a crystal oscillator. The two frequencies, Ie and fr are compared by a phase/
frequency comparator and a voltage is fed back via an active filter to the local oscillator. This feedback loop enables the frequency of the local oscillator, fo, to be phase
locked such that
fo = NAt _ _ _ _ _ _ _ _ _ _ (2)
n
where fx is the frequency of the crystal oscillator and n is the ratio of the fixed divider
that follows it.
The programmable divider is controlled by the channel selector. Thus, when a
certain channel is selected the selector would provide the required divider ratio code
to the programmable divider making the value of N to be such that fo becomes equal
to the required local oscillator frequency to receive the channel allowing for the offset
due to the intermediate frequency (IF).
Since each channel requires a certain band in the tuner, the channel selector also
provides the correct band select code to switch the tuner to the corresponding band.
The stability of the frequency setting of the local oscillator will be entirely defined
by
--n-
where Mx is the stability of the crystal oscillator.
We thus have a very useful system of tuning TV channels with the accuracy and
stability of a crystal oscillator.
With the simple system shown in Fig.2, the local oscillator frequency can be preset
to any value in steps of
37
BAND
SWITCH
Fig. 2 Simple practical synthesiser
Thus A and fr determine the value of the frequency step that can be achieved in the
system. The value of fr is dependant on the following factors:
1. the lock up time of the phase locked loop to the selected channel. Normally this
should be 200ms max.
2. the ripple on the varactor line should be low enough not to cause any noticeable
pattern on the screen.
3. the loop should not oscillate under any condition.
Considering these factors the value of fr is normally limited to 2kHz minimum.
Having decided on the value of ~ the value A is automatically set for a certain frequency step requirement in the system. For example, for a frequency step of 50kHz
and fr = 2.5kHz.
A=50 =20
2.5
Now the local oscillator frequency in a TV tuner can be up to 1000 MHz, and this
would mean having a programmable divider input frequency of
1000= 50 MHz
20
which is rather high.
The Key System Principle
The Key Synthesiser uses a two modulus divider after the prescaler and before the
programmable divider. This gives a much more manageable input frequency and control function. The modulus control is designed so that it can tolerate delay in the control loop and distortion in the control waveform. The positive going edge of each
control pulse is only used to change the divider modulus during one complete cycle of
its output. Fig.3 shows the block diagram of the Key Synthesiser.
The two modulus divider divides by a ratio, M, unless it has received a control pulse,
when it divides once by a ratio M-1. For each complete output cycle of the programmable divider there are N complete input cycles fed to it from the two moqulus
divider. If, during these N output cycles of the two modulus divider it receives P pulses
to its modulus control, it will divide by M - 1 for P output cycles and for N..:. P output
cycles it will divide by M. So for N output cycles of the two modulus divider, the
number of input cycles is:
P(M-l)+(N-P)M
After division by the programmable divider, + N, this number of cycles produces one
cycle at the input of the phase comparator.
When the loop is locked the local oscillator frequency, fa, is given by
fa = A [P(M-l)+ (N-P)M] fr
= (M.N-P).A.fr
(3)
An incremental change in the number of pulses, P, to the .modulus control will thus
change the local oscillator frequency, fa, by a step A.fr. In the Key System the prescaler, A, is +20 and the reference frequency at the comparator is 2.5kHz giving an
incremental frequency step of 50kHz.
38
Fig. 3 Simplified Key System Synthesiser Block diagram
The two modulus divider gives 7 19 or 720 so that the maximum frequency into the
programmable divider is only
fa
1000 MHz
A.(M- 1} = 20.(19} ~ 2.6 MHz
and the local oscillator frequency in equation (3) above now becomes
fa = N MHz - 50.P kHz
So N may be used to define a frequency as a whole number of MHz and P need only
have a value 0 to 19 giving 20 steps of 50kHz between values of N. In practice not
only does an original frequency need to be defined, but also any manual or automatic
frequency correction. This gives
fa = (0 + 1 - Oc}MHz - 50 (P + Pc} kHz
(4)
where 0 is the frequency number (10 bits)
Oc is the frequency number correction (3 bits)
P is the fine tuning number (5 bits)
Pc is the fine tuning number correction (5 bits)
The programmable divider counts down from the loaded number, 0, until it reaches
the correction number, Oc, when it takes one cycle to synchronously reload and the
whole operation repeats.
When a channel is entered initially
Oc = 4 and Pc = 0
so if TV channel 21 in standard G were required for example, then
0= 514and P= 17
which gives
fa= (514+ 1- 4}MHz- 50(17+ O)kHz
= 510. 15MHz
It is also possible to correction tune around the original channel frequency with a
range of -3.95MHz to + 4 MHz in 50kHz steps. This is achieved by using Pc to provide
a further 0 to 19 steps of 50kHz and Oc to provide 0 to 7 steps of 1 MHz. The values of
0, OC, P, Pc and the band selection code are obtained via the Keybus with the appropriate. tuning commands.
39
APPENDIX 2
KEY SYSTEM DEVICES
Typical
Supply
Typical
Voltage
Current
5V
90mA
5V
25mA
5V
12V
33V
12mA
9mA
4mA
5V
15mA
5V
20mA
5V
9V
35mA
ImA
5V
6mA
Synthesiser Block
CT2010
CT2012
CT2017
1 GHz, 2 Modulus Divider +380/400; 10mV
Input
PLL Synthesiser; crystal reference;
programmable divider; phase comparator.
Keybus (4 bit data highway & multiplex
clock) input.
Tuner interface-varicap control-station
detector; AFC control; power low detector.
Key System Control Circuit Options
CT2014
Digital Switch entry, Control IC.
Up to 32 programmes, 400 channels and 4
standards. Manual and auto fine tuning.
CT2015
Control IC with full remote control interface.
Up to 32 programmes, 400 channels and 4
standards. Manual and Auto fine tuning;
channel sweep. Keybus control.
CT1650AI
Microprocessor Control. 32 programmes,
PIC1650Z·20 100 channels and 1 standard.
Manual and Auto fine tuning, channel
sweep.
Key Circuits
CT2030
CT2031
CT2032
CT2033
Each CT2030 series integrated circuit is a
ROM for 100 channels with frequency and
name information via Keybus. Key 0 can be
interfaced with an ER1400 non-volatile
programme memory.
European PAL Key
European SECAM Key
North American NTSC Key
British Isles PAL Key
Programme Memory
ER14001
NC7400
Non-volatile memory, stores channel number, 9Vand-26V
transmission standard and fine tuning
OR
information for 32 programmes.
12Vand-23V
5mA
5mA
Remote Control
ML1900
ML1910
Remote Control Transmitter; 6 bit PPM; 56
codes; burst mode output.
Remote Control Receiver; 6 bit PPM; 56
codes; 55 code local input; 6 analogues with
63 levels; 32 programmes; total of 288
commands (via Keybus).
9V
Standby
5V
2mA
IliA
35mA
5V
3mA
Display Drivers
CT2200
*ML2040
32 Number LED Display Driver, drives two 7
segment common anode LED arrays, 5 bit
binary input; 1-32 display output, 20mA per
segment; 13 direct drive outputs.
On Screen Display, displays programme and
channel number, channel name, time and
day. Control via Keybus; display and
blanking output.
Miscellaneous
*ML2020
7 day clock, quartz crystal controlled; 12/24
hour with day, hour and minute settingoutput via Keybus or direct drive to LED
displays.
*ML2001
TeletextlViewdata Interface, allows Mibus
control from Keybus.
*Further details to be announced.
40
THE ROUTE TO
YOUR SYSTEM
Start with the Synthesiser Block
+
,-------_t------+-----i_-I
Interface
logic
Microcomputer
own design
ML2000
series
limited
choice
maybe
necessary
necessary
ML2000
series
limited
choice
YOUR OWN SYSTEM
CT2010. CT20I2. CT20I7
CT20I4. CT20I5. CTI650A
ML920 series, SL480, SL490
MLI900
MLl910
ML2000 series
CT2030 series
CT2200
Synthesiser Block
Control options (choose one)
Remote Control (see Consumer News Vo1.2, No.2)
Remote Control Transmitter
(K
5)
RIC Receiver and Keyboard Encoder
see eyway
Features Block circuits
Key circuits (ROMs)
5 bit binary input, 1-32 display driver
41
42
3. INFRA-RED
REMOTE CONTROL
43
44
INFRA-RED REMOTE CONTROL SYSTEMS
To offer remote control as a means of achieving additional sales is fairly widespread these days, with cost
prohibitive factor in some cases. At first, wired connections were used, and still are, for example, cheap
remote control toys, TV games, slide projectors etc. Then came ultra-sonics, and finally in the past few years,
the switch to Infra-red.
Infra-red systems offers several advantages over radio and ultra-sonic equipment in certain applications. No
licence is required-signals can be easily confined by walls - or directed by narrow beams. Infra-red
transmissions are not subjected to electromagnetic interference, infra-red noise is very rare in factories,
offices or houses and if the signal is modulated, then corruption by flicker is very unlikely. Radio links, on the
other hand, may be affected. by many sources of interference, and in some applicaions, e.g. toys, the
potentional hazard of aerials as a spike to a childs eyes should be avoided. Ultra-sonic links suffer from multipath interference and can also be affected by spurious noise generation, for example bells and jingling coins
or keys.
An infra-red link consists of a modulated source driving a light emitting diode which radiates at a wave length
in the infra-red region (850 to 970nm). The light is transmitted through an optical system which may flood an
area or concentrate the energy which is amplified and decoded to recover information that was transmitted. A
basic system is shown in Fig.1. Energy levels are, typically, only a few milliwatts and therefore harmless.
Applications have been developed for both nearrow and broad beam systems. Broad beams are used for
"anywhere in a room" controls, for example TV, teletext and viewdata controllers, garage doors, light
dimmers, toys, slide projectors and hi-fi units. The range for broad beam systems can be between 12 to 30
meters, where choice of emitter diodes, quality of components used and pcb design, will determine the
ultimate range obtained. Narrow beams on the other hand, are particularly suitable for industrial controls,
security systems, computer peripheral and TV transmitter links. The range for narrow beam systems may be
half a mile or more and, as these units can be designed to have a spread of no more than 10ft in 2000ft, and are
virtually independant of weather conditions, they are excellent for building-to-building work particularly in
data and TV transmission.
Plessey Semiconductors Limited have developed a range of remote control circuits tailored to various
requirements in the TV, Industrial, Professional and Consumer market sectors.
Data sheets on the various integrated circuits involved are available on request, together with suggested
circuits on a number of domestic applications.
Integrated circuits involved are as follows:SL490
Easily extendable 32 command PPM transmitter drawing negligable standby current
SL491
As above, but PPm transmission is in burst mode instead of in a continuous fashion.
SL480
Infra-red pulse preamplifier containing 3 amplifier stages, the g-ain of each being capable of
adjustment, to suit the application.
SL470
-
Capable of decoding up to 10 programmes and incorporates direct varicap voltage selection and
TTL level compatible inputs.
The following are Receiver chips that demodulates the PPM signal transmitted by the SL490/491.
ML920
20 programme memory, 3 D/A converters plus 6 other facilites.
ML922
As above, but with only 10 programme memory.
ML923
16 programme memory, 1 D/A converter plus 6 other facilites.
ML924
5 digital outputs whose response to PPM codes be programmed by 6 control lines. Has a
handshake inte-rtace-which provides communication with microprocessors and computers.
ML925
Designed to control either a toy vehicle with 2 speed drive motors and a three position latching
steering system, or a vehicle with momentary action steering and a third motor, typically a
winch.
ML928/9 -
General purpose receivers, latching 16 of the 32 codes transmitted by the SL490/1.
ML926/7 -
As above, but with unlatched outputs.
The ML928 responds to codes 00000 to 01111 and the ML929 to codes 10000 to 11111.
Other components needed for an infra-red system are the emitter diodes and the photo diode.
45
The photo diode used is a highly critical component. Several manufacturers have developed photo diodes for
use in the infra-red region-the characteristics of one such device is shown in Fig.2. This is a low leakage p.i.n.
device with planar construction; the active area is 7.5mm 2 • A silicon nitride layer over the chip acts as both a
passivating coating and an efficient anit-reflection layer. A dye in the plastic housing transmits well in the
near infra-red part of the spectrum (700nm t011 OOnm), but is strongly absorbant to visible light (400nm to
700nm). The spectral response of silicon, in addition, is higher in the infra-red than in the blue green region.
Planar construction keeps the reverse leakage current low, which is very important in small signal
applications.
Usable signal to noise ratios can be achieved with photo current as low as 10nA provided the load is carefully
chosen.
Many alternative infra-red high efficiency L.E.D's are available; typical emission characteristics are also
shown in Fig.2. Increased sophistication of epitaxial techniques is likely to mean that increased power
conversion efficiency will be available over the next few years. It is usual to drive these L.E.D's with pulses of
current which peak at much higher than rated values, keeping the duty cycle such that mean rated power is
never exceeded. In this way transmission distances are increased.
>r-
SHADED AREA REPRESENTS
VISIBLE RADIATION REJECTED
BY BPW41
;;
~/
i=
iii
z
/8X4
ill
~
KEY PAD
r-
:::l
D-
r-
:::l
o
ill
NORMAL
SILICON
PHOTO
DIODE
>
i=
..:
....J
ill
ML920
SERIES
PHOTO
DIODE
IT:
AMP
DECODER
WAVELENGTHS
IN nm
Figure 1.
400
500
600
700
BOO
900
1000
1100
1200
Figure 2.
Transmitter Chip SL490
Fig.3. shows the circuit for a simple infra-red transmitter where the PPM output pin 2 ofthe SL490 is fed to the
base of the PNP transmitter TR1 via R1 and R2, producing an amplified current pulse in the collector about
15usec wide. The pulse is further amplified by TR2 and applied to the infra-red diodes D1 and D2.
The current in the'diodes and the infra-red light output is controlled by the quantity, type, and connection
method of the diodes and also the gain at high currents of the transistors.
The common solution where cost is important is to use 2 single chip diodes, such as the Siemans CQY99
CONNECTED SERIES.
Improved output can be obtained by using four CQY99 diodes in a series parallel arrangement, but is usually
simpler to use 2 multi-chip diodes such as the Telefunken CQX47 connected to parallel or single CQX19
which gives similar results.
A significant increase in range can be obtained by using diodes such as the CQY99 in conjunction with a
plated plastic parabolic reflected
When building the transmitter, care should be taken with the choice of the capacitor C2 and with the circuit
layout, particularly when multi-chip diodes are being used, as the current pulses can be as high as 6to 8amps.
46
Transistor choice is also important and any substitues should have high current gain characteristics and
switching speeds similar to those specified in Fig.3.
An increase in output can be obtained be reconnecting TR2 in a common emitter mode, but care should be
taken not to exceed the rating of the diodes.
Choice of PPM Frequencies
Although the ML920 series of remote control receivers is designed to work over a wide range of PPM
frequencies, the actual usable range may be resricted by the application. The analogue outputs on the ML920,
ML922 and ML923 serve as a good example, since the outputs will step up or down, one step for each pair of
PPM word received. This in turn fixes the rate of increment or decrement of the volume or color controls of a
TV set.
When the transmitter is being used with an infra-red link, with high current pulses fed to the diodes as in Fig.3,
power consumption will increase with frequency. It is thus advisable that with a battery power supply, the
slowest PPM rate consistant with adequate response time, should be chosen.
Setting Up Procedure
When designing a system using the SL490/491 transmitters and the ML20 series receivers, it is not necesssary
to adjust the PPM rate on both transmitter and receiver. The usual arrangement is to have a fixed resistor of
33K from pin 16 of the SL490/491 and to choose the capacitor connected for pin 16 to pin 17 to give the
required PPM rate. The value is calculated from the formula 'to' = 1.4CR. Provided fairly close tolerance
components are used for C1 and R1, then assenbled transmitter units should be interchangeable without
adjustment.
The timing components on the receiver can be selected using the formula frx
being the P.P.M. logic "0" time from the transmitter.
=
1
0.15CR
where frx= 40 ,'to'
'to'
The value of R for the receiver should be between 47K and 200K, a typical arrangement being to use a 47K
resistor and a 100K pot as shown in Fig.4. The capacitor should be selected from the above formula to give the
nominal frequency somewhere near the mid-range setting of the potentiometer.
Final adjustment is made by setting the period on the receiver oscillator time constant pin to 1/40th of the
transmitter P.P.M. logic "0" time using the potentiometer. Connection to the receiver time constant pin
should be made using a x10 oscilloscope to reduce circuit loading.
When adjusting the ML920, the monitor output can be used for setting up, but in this case, a figure of 1/20th of
the transmitter P.P.M. logic "0" time should be used as the mirror output is at half the oscillator frequency.
+9V
R
33K
SL490
2%
C1
68n
16
C=f:
17
2
18,......
1-
5%
;----
4.7J.l
r
R1
100£1
l¥TR1
'~
2K2
D1
D2
Fig. 3.
TR2
BD437
"::::I C2
:: 1501-'
~:
Infra-red Transmitter
47
ov
C1
68n
T
D1
R1
1000
--;r-+-~
D2
ML920
SERIES
RECEIVER
C2
150f,l
OSC. TIC
PIN
47K
~
R3
1K
OV
ov
Fig. 3.
Common Emitter Arrangement
Y100K
Fig. 4.
Recommended Receiver Time Constant
Components
The SL480
The circuit diagram of the SL480 infra-red pulse amplifier is shown in Fig.5. Pulses generated by a infra-red
receiver diodes are amplified to a suitable level for direct connection to the input of any of the Plessey
Semiconductors ML900 series of remote control receiver circuits.
For basic operation, the receiver diode and SL480 input is biased with a single resistor to the positive supply as
shown in Fig.6. Any infra-red light reaching the diode generates a leakage current which causes a voltage
drop across the bias resistor.
The SL480 Input stage consists of a compound emitter follower (TR1 and TR2) which provides a high input
impedance and allows a relatively high diode load resistor as well as a voltage drop of around 1.3V between
the input and the bases of the first amplifier stage (TR6,TR7).
Transistors TR6 and TR7form a differential amplifier which is designed to prevent low frequency or D.C. input
signals from reaching subsequent stages of the amplifier. Since the bases of transistors TR6 and TR7 are
internally connected by the 6.3K resistor R3 low frequency signals are applied to both sides simultaneous
causing no change in collector current and therefore no output to the second stage. Higherfrequency signals
are amplified because TR7 base is decoupled externally on pin 7.
Stage 2 gain is provided by a similar differential amplifier to stage 1 except that the relativly stable d.c. input
voltage provided y stage 1 output allows the use of a tail resistor R11 ratherthan a current source. Decoupling
of A.C. signals is provided at pin 8.
Stage 3 is similar to stage 1, but with a extra current mirror (TR24 to TR26) to provide signal inversion at the
output
The standing current in the output load resistor and thus the output voltage, is set by the current in R15. This
current will amount to about 100llA, and give an output voltage about 5V below the positive rail with a 15V
supply.
It should be noted that there is a parasitic zener diode of about 6V in parallel with the ouput load resistor R19,
this will be destroyed if the output is shorted to the negative supply rail. Stage 3 decoupling is provided at pin
1.
With a 15V supply, the input stage will operate with input voltages ranging from 15volts down to 5volts. This
will allow the device to function satisfactorily in high ambient light conditions which produces high leakage
currents in the receiving diode. A single transistor circuit is shown in Fig.3, which prevents the input voltage to
the SL480 changing for diode leakage currents up to several miliamps. By carefull choice of R & C values, this
circuit can be made to give extra rejection of low modulation such as that produced by incandescent lamps.
48
If required, the gain of each of the SL480 can be set individually by connecting a resistor in series with the
decoupling capacitor. A 6K resistor will reduce the stage gain to half its full value of about 40dB. Normally it is
only necessary to reduce the gain of the second stage with about 33-56K.
As with any high gain device, care is needed in the layout of printed circuit boards to prevent instability. All
decoupling and input components should be mounted close to the SL480.
Oecoupling of the power supplies local to the SL480 is advisable. Aresistor of about 560 n in series with the
negative rail and a parallel capacitor of 68~F being adequate (See fig.7).
The decoupling resistor should always be in the negative supply as the ML920 series remote control circuits
have a threshold close to the positive rail, and any voltage drop here would reduce the noise immunity.
1:1
TA')i---,..-+-'::.:"-I---K
A'9
52K
liP 0----1:'" TA'
alP
6.3K
260
260
570
2
570
A6
146K
A'
300K
A2
150K
A7
146K
TA3
A.
150K
A11
66K
A13
132K
A,.
150K
Figure 5.
+
BPW41
5
)J1
56K
Fig. 6.
SL480 with simple bias for the Detector
49
OV
47n:
,. BC307
82p ::
:~
lOOK
SL480
BPW41
5 ............
"~""~
GAIN SET RESISTOR,
10K TO 100K
(HIGH GAIN) (LOW GAIN)
2n2 ::
T
33
1J
5600
-16V
1.5mA
Fig. 7. Typical Infra-red Amplifier application with ImprovedDetector Biasing.
50
4. REMOTE CONTROL
FOR TOYS
51
52
The new remote control circuits now available are the SL470 10-programme decoder for high voltagevaricap
line drive; the SL490 infra-red preamplifier with direct drive for the ML920 series; the SL490 remote control
transmitter; the ML920
The new remote control circuits now available are the SL470 1O-programme decoder for high voltage varicap
line drive; the SL480 infra-red preamplifier with direct drive for the ML920 series; the SL490 remote control
transmitter; the ML920 20-programme remote control receiver; the ML922 remote control receiver providing
three analogue outputs, 10 latched programmes and on/standby, mute etc; the ML928 remote control
receiver/encoder providing four latched outputs controlled by 16 transmitter commands; the ML929,
basically similar to the ML928 but operating on a different set of 16 transmitter commands; the ML926, similar
to the ML928 but giving momentary, unlatched outputs; the ML925 for motor control in toys and models and,
available soon the SL491 for burst mode transmission.
SL470
This device decodes up to 10-programmes, incorporates direct varicap voltage selection and TTL level
compatible inputs. It can be directly driven by the ML922 receiver and has a low component count for low cost
applications.
SL480
The SL480 is a bipolar integrated circuit containing three amplifier stages. Its output is directly compatible
with the ML920 range of remote control receiver circuits, and it is in an eight lead plastic package. A feature of
the device is that the gain/bandwidth of the amplifier stages can be adjusted to suit the application (see Fig.1).
Pin functions, SL480
1. Decoupling point
2. Output decoupled with capacitor and fed directly to receiver PPM input.
3. Positive supply
4. Detector input
5.
6.
6.
7.
8.
Not used
Negative supply
Negative supply
Decoupling point
Decoupling point
SL490
The SL490 remote control transmitter is an easily extendable 32 command, pulse position modulation
transmitter which draws negligible standby current. It can be used effectively with any ML920 series remote
control receiver.
The ML490 pulse-transmitting remote controller, used in conjunction with the ML920 receiver offers the
possibility of controlling up to 20 television programme selections, brightness/volume/color control in up to
32 steps, and a number of other functions both for television use and elsewhere.
A wide variety of domestic, commercial and industrial appliances can be controlled by the SL490/ML920
combination. Apart from use with television and toys the system can control such diverse equipment as, for
example, radios and tuners, tape and record decks, garage doors, automatic telephone answering machines
and slide projectors.
ML922
This device demodulates the PPM (Pulse Position Modulation) signal received from the SL490 transmitter.
The ML922 was originally designed for television remote control systems but can easily be adapted for use in
radios, tuners, tape and record decks, lamps and lighting, industrial control and monitoring, and toys and
models.
The ML922 demodulates the PPM signal received from the SL490 and after error checking the received code
can condition a 10-programme memory or one of the three D/A converters, the output of each having its
normalised level at three eighths of maximum
53
The receiver timing can be set by adjusting the oscillator time constant to give 40 periods atpin 6 equal to aD
interval on the received PPM input.
ML920
The ML920 is a 20-programme version of the ML922, but has (in addition tothefacilities offered by the ML922)
a 'recall' output which can be used to trigger an on-screefl display in TV applications.
ML928 and ML929
Both these devices are general purpose remote control receivers each designed to receive and latch 16 of the
32 codes transmitted by the SL490 circuit as 5-bit PPM.
'
The ML928 responds to codes 00000 to 01111 only, and the ML929 responds to codes 10000 to 11111. Both
devices are packaged in 8-lead plastic DIL to minimise board area. The on-chip oscillator can be adjusted
from 15Hz to 150kHz, allowing different transmission rates.
Both devices have a high degree of immunity to incorrect codes; there must be two correct and consecutive
codes received before the outputs can change. As with ML922 these devices were initially designed to be used
with television remote control. They have, .however, a wide range of applications, particularly in toys.
ML926
This device has momentary outputs. Normally low (off) selected outputs go high (on) during reception of the
appropriate code. After transmission has finished the outputs return to the low state. The device is similarto
the ML928 except for its four positive logic unlatched outputs.
ML925
Up to three independent motors, as well as lights, flasher and horn, may be driven by this 18-pin device. Four
speeds are possible with both forward and reverse giving a very flexible toy or model controller.
+
t
+
I
~vcc
Fig.1 SL480 high gain pulse preamplifier
54
SL490 remote control transmitter
General description
The SL490 is an 18-pin bipolar, remote control, pulse transmitting monolithic circuit for use with the
ML920/M L922/M L926/ML929/M L925/ML926 receivers.
Single pole switches arranged in a 4 x 8 matrix of 32 keys (1 out of 4 and 1 out of 8) are encoded by the device
which then may give either a modulated carrier frequency from an on-chip oscillator or a DC pulse output. A
standby current of only 6uA or so is taken from a 9V supply by the device until any switch closure is detected.
In this system of PP3 battery has a working life approaching the length of its shelf life.
The modulated output can drive an ultrasonic transducer directly and be tuned to the natural resonant
frequency of the crystal, thus enabling inexpensive transducers to be used.
A five-bit pulse position modulated signal is used, giving 32 basic commands which can be used in a TV
remote control system to select 20-programmes, control 3 analogue functions and provide 6 additional
switching functions.
Apart from the battery, switch matrix and transducer, only three capacitors and two resistors are needed
externally. A single RC selects carrier options and defines frequency, the other RC defining the modulation
rate.
Output capability is direct ultrasonic transducer feed, and complementary outputs with or without active pullups. Continuous or pulsed visual indication can be driven directly from pin 2. The carrier oscillator can be
disabled for pulsed operation of infra-red, and more than one set of 32 commands can be used by changing
the modulation rate and carrier frequency.
Despite the comprehensive range of facilities offered by this remote control system, the SL490 makes the
transmitter a very simple unit. Fig.2. outlines the block diagram of the transmitter.
Circuit Operation
The device transmits a code word as a group of six pulses, and each ofthefive intervals between these pulses
can take up one of two possible values, a short interval corresponding to a '1' or a long interval corresponding
to a '0'. Fig.3 shows the timing relationship between the pulses '1', '0' and'S' - the space or synchronisation
gap between words.
The ratio of the intervals representing '1', '0' and'S' is 2:3:6 and is fixed by the device. In addition the width of
the pulse is about one sixth of a '1' interval or 1/3:2 on the above ratio scale. In this way 32 different codewords
can be transmitted by the 5-bit code.
A particular codeword is selected by switching one out of four current sinks (one of these current sinks is OV).
All decoding is done by the integrated circuit as in Fig. 2.
The circuit draws only about 6uA from the supply until a switch closure is detected, at which time power is
applied to the whole circuit. The appropriate PPM code is then generated repeatedly until the switch is
released, and the device reverts to standby after the complete codeword has been transmitted.
Fig. 4 and 5 show the output voltage waveforms obtainable. Fig.4. shows a lower than normal carrier
frequency compared with the pulse width. This is done for clarity although the device would operate
satisfactorily with such timing.
For infra-red operation a two transistor amplifier is used to feed very narrow high current pulses to gallium
arsenide infra-red diodes, such as two Plessey GAL32B. If a higher output is required three or four GAL32C
diodes can be used in parallel. The pulse nature of the signal allows the diode emitter to work at a higher light
output efficiency and the battery current to be reduced. Fig.12 shows a circuit for driving infra-red emitting
diodes.
The receiver amplifier
At the receiving end of the link the system will need some sort of gain and bandwidth defining stages, before
the detected signal is fed to the ML920 series receiver. Usually two, or at most three, amplifier stages are
sufficient with some fairly simple active filtering. In the case of the infra-red link the SL480 can be used with
an infra-red filter before the photo detector.
55
For ultrasonic transmission a general
purpose operational amplifier may be
used for the front end. After filtering
and amplifying the ultrasonic
frequency, a simple diode detector can
be used. The detected PPM can then
be fed to the receiver via a buffer
amplifier stage. An ultrasonic
frequency of between 32kHz and
44kHz should be chosen to avoid the
second and third harmonic of the TV
line output stage. An inexpensive
transducer can be chosen with its
natural resonant frequency within this
band, and can be driven at its natural
resonance to improve power output
and simplify loading. The actual
bandwidth needed about the carrier is
approxi mately 100Hz. The data rate
can be chosen by considering the rate
at which the analogue outputs of the
receiver are required to step.
If, for example analogue output to
sweep its full range of32 steps in about
10 seconds, this requires one step
about every 300ms but because of the
receiver error checking code
comparator, the transmitter word rate
should be set to 150ms (see Table 1).
Referring to Fig. 3 it will be seen that if
the code word period, including the
interword space, is 162ms it will give
the required analogue full range
change in about 10 seconds. The only
adjustment needed in the receiver is to
set the oscillator time constant, so that
40 time periods on the oscillator (20
periods on the monitor pin 9 of the
ML920) corresponds to a±O± interval of
incoming PPM (Fig.6 and Table 1).
Up to 10 per cent variation in
demodulator timing oscillator
frequency can be tolerated by each of
the transmitting and receiving devices.
SwIT1:...
,------------,-i
c.-....
~
s ........
~v.Im:14
11.!...",.I-r..,.------Inril YIbu..
Ov
Fig.2 Transmitter SL490 block diagram
>4~~
-H~~
-ll- I
3ms
C"'rri~r
or
HI-----~~
'I~'
IS",,~
27ms
1KHZ
m"~
be.
+r"nsmif+"d
'I
54ms
over
tilephon .. lin~&
Fig.3 Ultrasonic carrier transmission
,
.
o
- - - + - > TIME
"
PIN3
-
t
Fig.4 PPM output showing ultrasonic carrier frequency
lJ
u
Fig.5 PPM output (pin 2) with no carrier
56
---CODE WORD I - I N T E R WORO GAP
PIN2
CARRIER)
--
~
CODE WORoa
~
(NO
LJ
~
0
- - - - - - --
40 pt.riods
of receivtr
-
- -
--~
oscill6tor
Fig.6 System timing
'0' period (ms)
TX cq.lF)
AXC (nF)
40
20
10
5
2.5
1.25
0.625
0.312
0.82
0.47
0.22
0.1
0.047
0.027
0.015
0.0068
100
68
33
15
8.2
3.9
1.8
0.82
Osc. (kHz)
1
2
4
8
16
32
64
128
Table 1 TX and RX Timing
An infra-red link
For most remote control work, infra-red links have advantages over ultrasonic links-less multipath
interference, lower spurious radiation, less annoyance to humans and animals, a higher modulation rate
capability and more robust transducers. High efficiency, infra-red, light emitting diodes (LED's) are relatively
inexpensive and can incorporate both reflctor and lens for a more concentrated beam of light.
Multichip assemblies are also becoming more common and these can take fairly high currents. LED's become
more efficient at higher currents, and pulse and multiplex systems are common for display work. Thus a PPM
system can be made to operate an LED at quite high outputs for a small increase in battery current. Two or
three LED's can be connected in series at lower currents, and these emitters can have different orientation on
their axes if required.
On the receiver side a photodiode or phototransistor can be used with an appropriate infra-red filter. Fig.?
shows how a photodetector response, although peaking in the near infra-red region, has good detection
properties at visible light wavelengths and into the ultra-violet. As the energy emitted from a gallium arsenide
LED is, in the main, a narrow band emission at 940nm, a correctly chosen filter will greatly attenuate most of
the interfering signals. Other noise sources which have large emissions in the infra-red (for example a
tungsten filament lamp) can be rejected by filtering or by carrier modulation of the infra-red link.
Both amplitude modulation and frequency modulation have been used, but neither has the simplicity nor all
the advantages that a pulse system can offer in LED driving efficiency and detection economy. Pulse position
modulation using a narrow pulse, high current drive to a gallium arsenide LED enables a very good signal-tonoise ratio to be obtained at the demodulator. Reception remains uninterrupted by most external influences.
Very bright sunlight or the close proximity of a high output fluorescent gas discharge tube has a minimal
effect, especially in the case of the SL480 with its daylight bias arrangement (see Fig.9).
57
'00
nMSMIUIOM
ILFORD 207
(%)
SILICON
PHQTODf.TltTOR
80
60
40
20
03
0·5
04
O'b
0-7
0·8
WAVELENGTH (AAITI)
0·'
,.,
'·0
'·2
Fig.7 Optical response cnaracteristics
4"':::
&t307
1001t
.,:;: 1
P
..
~ ~W4'
BPW 41
.
p
OR
•
: ~,"1
2n.~
v
OUTPUT
+
p~~~sa~~ (
KODA.K
FILiER 87c
0
TAl'
,1"
. .....---
_Go:m SI.+
re.s.istor.
10K. TO 100K
(KI'"''''I", (UI"'."I"')
SIMILA.R
T··. .
5bOn.
-16"
,·5mA
Fig.8 SL480 with simple bias for the detector
Fig.9 Typical I R application with improved detector biasing
SL480 infra-red pulse preamplifier
The SL480 is a low cost, low external component count, front end amplifier for infra-red pulses (see Fig.8 and
9).
.
It has three gain stages, each with a gain 100, and differential inputs with inverting input bonded out to provide
access both for decoupling and frequency determination.
Input impedances are typically 6k ,enabling the amplitude and frequency response to be defined by only a
few capacitors an,d resistors.
The output of the SL480 can be fed directly to any ML920 series receiver and gives a positive pulse. A positive
common supply should be used between receiver and amplifier for best noise immunity.
The diode is reverse biased and conducts a small leakage current only, the current increasing as light falls on
the diode.
All SL480 series devices accept supply voltages from 5V to 18V and have low current demand, typically 1.5mA.
The overall gain is generous; at least one gain setting resistor should be used to avoid any instability
problems.
58
Applications
Fig.10 shows a typical remote control system for infra-red control of a 10 programme television set. An
additional SL490 in the set gives full control from the local position as well as the remote keyboard so push
button control of the programmes and color brightness and volume is achieved on set. However, such a
system may equally simply be applied to industrial communications or model areas with similar advantages.
~
_ _ _ _ COL.OUR
~
_ _ _ _ BRIGHTNESS
INFRA-RED
(OR UL.TRA-SONIC)
VARICAP
CONTROL.
AFC
DEFEAT
SELECT
LOCAL CONTROL
Fig.10 A typical remote control for TV
The transmitter
As mentioned previously a digital
pulse mOdulation system may be used
on almost any link; ultrasonic, infra·red,
radio or cable. Figs.11, 12 and 13 show
how the SL490 may be applied to three
different types of link with very few
additional components. In Fig.11 low
cost transducers may be used and the
transmitter carrier may be tuned on pin
18 to the narrow band resonance point.
The complementary output of the
device gives double the drive to the
load. A fixed value of RC timing has
been used at pin 16 to give a data rate of
about 6 words per second, necessarily
slow for a simple ultrasonic system.
The infra·red transmitter (Fig.12)
uses a pulse output with no carrier,
from pin 2, at a rate of 20 words per
second. C3 and R2 allow the comple·
mentary pair, TR1 and TR2, to conduct
for about 151's at every negative leading
edge of the PPM waveform. Pulse
currents of up to 6amps have been
achieved with such a circuit but care
should be taken to minimise the
impedance of the current path. Connections should be made as short as
possible and C4 should be a low
inductance type.
When simultaneous operation of
more than one transmitter is required
(e.g. video games, model racers etc.)
8x4
PP3
+
1J-----'=:r1
10K.
TO'"
(A01uST
FREQUENCY
TO SUIT TR--.N60UCE.P..)
Fig.11 Ultrasonic transmitter direct drive
59
each signal should be periodically interrupted to allow the other access without jamming. This may be
achieved by an externally generated waveform applied to pin 16 of the SL490 or by using the newly developed
Plessey Semiconductors Burst Mode Transmitter, the SL491. This circuit has a modified second oscillator on
pin 18 to allow mUlti-transmitter burst mode operation.
In the radio control transmitter in Fig.13 the internal carrier oscillator of the SL490 is inhibited by a resistorof
2.2k
at pin 18. The negative pulse output at pin 2 is then used to key a 27MHz crystal controlled
oscillator/output stage. The total quiescent current is a few microamps and even when keyed at 50 words per
second the duty cycle is only about 15% .
The transmitter will enable both indoor and outdoor operation of various toys and models. A third transistor
stage may be used to increase the range.
Various receivers are of course possible, from a multi-channel crystal controlled synthesiser superhet to a
three transistor type shown in Fig.14 with just RF amplifier, regenerative detector and output stage which may
be directly connected to any ML920 series receiver.
The ML928 remote control receiver is used in this circuit, suitable for controlling tracked models such as
military vehicles or earth moving equipment. Either relays (Fig.15) or transistor switches (Fig.16) may be
used.
s~
4
KE.YPAD
101
~/
110
/
010
PLESSEY
001
SL490
000
10
01
c.
T:~7f
.1.
RI
.""
pp3
Ie,
Fig.12 Infra-red transmitter
Fig.13 27MHz model control transmitter
60
Responding to codes 00000 to 01111 only, the ML928 receives and latches 16 or the 32 codes transmitted by
the SL490 remote control transmitter. Fig.17 shows how the SL480 interfaces with the ML928.
In the field of military models, the tank is a pacticularly good example of a two-motor application for this
circuit. Both tracks can be independently controlled, together with (for example) turret rotation and cannon
elevation, giving the model accurate scale operating characteristics and versatility.
However, for a more complex control involving up to three motors, lights, flasher and horn the ML925 can be
used.
I
r-~--~-r--~----------~----T--+
(§) @ @
@) @) @
® CID ©
Fig.14 Typical 27MHz receiver for toys
STOP
L.EFT rOkWAIlO
0
0
l
I
I
I
I
I
e.OTK fOIlWoUla
0
0
I
0
,
TR,A.NS'""'TTII!.R.
P.14HTI'O"WA/t.O
0
I
I
0
I
COCES
LI!IfT ""IN
0
0
I
,
0
'''GHoT a"l"
0
1
0
0
I
Lin
"I.n~[
"'tv......
0
I
0
0
,
0
,
0
II,IOI(T R,IlVIEItII
0
I
•
1
0
60TM
I
,
Fig.15 Relay control of 2 drive motors
Time proportlonai or 3-posltlon steering
Not only does the ML925 give a multi-function control capability but also several working modes are possible.
Two similar models may be operated independently with burst-mode transmission and two sets of command.
Fig.18 shows how the ML925 may be used in an infra-red control system for a truck. The supply rail (pin 1),
oscillator (pin 2) and PPM input (pin 3) are standard ML920 series specification. Motor control outputs to
'steering' and 'winch' are momentary outputs while 'drive' is a latched outputs. Only one output pin of the
motor drive pair will go high at anyone time to give a forward or reverse sense and the 'no-drive' condition
exsists when neither pin is high.
An additional oscillator at pin 6 is used to give a flashing output at pin 5 or pin 4. It also produces three different
chopped waveforms at the 'drive' nad 'steering' outputs so that four different speeds are possible. Other
outputs that may be toggled on or off are 'lights' (pin 13) and 'hazard' (pin 4) which gives a flashing signal.
'Flasher' (pin 5) is a permanently flashing signal and 'horn' (pin 18) gives a momentary output. Pin 15 is used
to select either one of two command sets for simultaneous control of two toys.
Another type of model may use 3-position steering where a center position is needed as well as full left or full
right. Fig.18 shows how this may be achieved very simply with the ML925. The center steering position is
marked by an insulated section with positive and negative supply rails at either end. The sense contact is wired
to the steering feedback input (pin 14) of the chip which can then quickly decide to center the steering from
either full left or full right positions. For this facility the 'vehicle type selct' input (pin 12) is connected to the
positive supply.
'Minimum components' ML922
Fig. 20 shows a simple IR television control using the ML922 remote control receiver. The system provides
three primary functions; power, programme and sound. Other functions-mute, step (up or down) intersation
AFC defeat, interstation mute-are also available if required.
Oscillator timing is set up as usual with a resistor value of about 50K. The exact value is established by preset
adjustment.
This circuit, together with a 5-command transmitter (Fig. 12) gives a low component count, low cost remote
control system for analogue and digital functions.
61
·t
IH414&
IN4148
~I
F(L'U.Q,'~
,.
!O, .. , lUI
-16'4'
Fig.16 6V 1A transistor motor drive
Fig.17 Compact infra-red receiver
...
Fig.18 Infra·red drive for car or truck
,.
PLESSEY
ML925
11
10
Fig.19 Infra-red drive for car with :J.position steering
62
. . "'I
10 ... A.
5bOl\
L---------~----------~--L-~--_r~O,
Fig.20 Simple IR TV control
63
64
5. ELECTRONIC
TOUCI-I CONTROL
65
66
Introduction
Electronic touch selection was initially incorporated into TV tuners to overcome most of the difficulties
associated with mechanically interlocked switches such as unstable contact resistance and misoperation of
the mechanical latching mechanism. These problems increase as more channels are needed and as
electronic varactor tuning was introduced electronic touch selection was a natural, partner development.
The primary requirement of any touch system is to sense the impedance of a finger across two selection
contacts. A memory and display facility is then used to remember the last selection made and indicated this
state. All previous selections are usually cancelled. Such selection systems have beedn used not only for TV
touch tuning but also in FM stereo tuners and AC power control although the major commerical application
by far is the TV market especially where European consumers are requiring more than 12 programme sets.
The reliability hazard of a multiple interlinked mechanical system becomes acceptable. A single chip solid
state solution is very attractive. Such a system will require each TV channel to have
1. A touch sense input.
2. An output for varactor tuning.
3. A channel indicator.
Other facilities required may be stepping mode for a remote control option, the ability of system expansion by
cascading units, a muting facility for the sound channel and disabling the AFC during the selection change, a
preset state of switch on and possibly a band switching function.
The ML230 Series
Plessey Semiconductors have developed a series of low threshold P-MOS touch control devices to cater for
the majority or requirements. MaS integrated circuits are ideally suited to the high impedance input
requirements of touch sensing circuits. A higher order of integration is achievable with MaS technology so
that all requirements may be realised with a single device. A high noise immunity and a very economic supply
current ma~e these devices ideally suited to TV touch tuning.
The basic touch sensing, laching and output configuration is shown in Fig. 1. Apositive sense input normally
has a voltage which is more negative than O.6(V DD-V SS) on one of the channel touch sensing inputs. A
simplified representation of the circuit is shown in Figs. 2 and 3. A voltage comparator with a threshold
voltage of O.5(V DD-V SS) is used to set the channel bistable memory and reset all other channels. One output
transistor then enables the varicap output line for tuning while the other holds the input at V SS and possible
drives an indicator. The varactor supply and output are separated from the main device sensing circuit and
slection logic supply in all ML230 series devices, so that nothing need interfere with the tuning voltage
regulation. The 'ON' resistance of the varicap outputs in guaranteed to be less than 1000hms at 10mA for.
devices in the series.
Table 1 shows a range of Plessey Touch Selection devices and lists some of the different facilities they offer.
ML231B ML232B ML236B ML237B ML238B ML239B
Number of pins or package
Number of channels
Neons(2)
LEDs(')
Sensitivity, RF ( 100M, Mains)
( 5OM, High DC)
( 20M, Vss DC)
Channel Selection, + ve
-ve (GND)
Stepping Facility
Mute alP
Clear liP
Cascadable
Channel Selected, Power Up
Band Selection l ')
16
6
Yes
Yes
Yes
Yes
Yes
Yes
-
16
6
Yes
Yes
Yes
Yes
Yes
Yes
-
-
Yes
-
-
-
3
Yes
Anyl61
Yes
24
6
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Anyl61
Yes
18
6
Yes(1)
Yes(3)
Yes
Yes
Yes
Yes
Yes
Yes
24
8
Yes
Yes
Yes
Yes
Yes
Yes
-
24
8
Yes(')
Yes(31
Yes
Yes
Yes
-
-
Yes
Yes
Yes
Yes
Yes
Yes
Yes
1
Yes
-
-
1
Yes
1
Yes
NOTES
1. Neons with a ± 10% tolerance on striking voltage.
2. Neons with a ± 20% tolerance on striking voltage.
3. LED's used at a current below 5mA.
4. LED's used at a current below 10mA.
5. With Neons or LED's at reduced sensitivity.
6. Some external components are required.
TABLE 1. ML230 Senes
67
RESET TO
OTHER CHANNELS
RESETS FROM
OTHER CHANNELS
VSV IVARICAPI
....1_~_+VDD
VARICAP O/P.
SENSE liP
Fig. 1 Basic channel arrangement of a
multichannel touch selection device.
O.SIVDD-VSSI
VSS
RESET
OUT
VSV
CHl
Fig. 2 Part of a touch control showing
channell only.
REF
-...ELl
a
I
RESET
OUT
I
,
I
1
-'~L_EL.J~LRESETS FROM
I
I
I
I
CH2 'I CH3 " CH4 " CHS " CH6 "
RESETS
FROM
OTHER
CHANNELS
,
,
I"
I
I I I
,
,
I
'I
CHANNELS
1
6
VSS
--b
L ___ JrT
H_I ~ T_j'
ili-~~w~~
r.1
Fig. 3 Basic 6 channel touch selector,
ML231.
68
Design considerations
The ML230 series of integrated ciruits can be easily designed into many applications and internal protection is
included, but resonable care should be taken as with any other M08 device particularly before and during
connecting the device to the external circuit. The in dependant V 8 varicap supply should not exceed V 88 and
for optimum drive should not be less than V ss -0.7V. All devices are tested at 30V and 36V and some
applications exist where successful performance has been achieved with V 88'-V DO =16V.
Touch 8ensing
The requirement of the touch sensing inputs is to sense safely a finger resistance which could be over
20Mohms. B8415 suggests a comfort limit of 0.3mA peak and specifies a safety limit of 0.7mA peak current
flowing between any accessible conductor (in this case the touch plates) and any other externally fed
conductor (in this case 240V 50Hz). Thus a minimum resistance, R1, can be calculated:RI
=
240 x f f
k ohms
0.7
485 kohms
Also the maximum leakage of the ML230 series inputs is specified as 1M A, the input leakage resistor, R1, in
Figs.4(a) and 4(b) has to pass this leakage current without allowing the input of the device to approach too
closely to the sensing threshold.
Minimum input threshold voltage=O.4 (V DO-V 88). Choose a safe limit of input voltage, e.g. V DO +10V.
R1 = 10V =10Mohm
1M A
Fig.4(a) shows how a touch sensing circuit may be arranged to operate using the 33V or so of the device
supply. R2 and R3 are both safety components needed in the case of unisolated, usual, television chassis
arrangement. A lower finger resistance will be needed to be sensed by such a low voltage circuit. Let this
maximum worst case finger resistance be Rf. Then for sensing at the highest threshold:Rf+ R2 +R3 = 0.4
10
0.6
Therefore Rf =5 ..5M
This sensitivity is adequate if good touch contacts are used but he arrangement shown in Fig.4(b) will provide
better sensitivity. In this case
Rf +16.8=240./2
2
Thus Rf = 150Mohms
It will be noted from Table 1 that two devices. ML237 and ML239 are available fortouch selection by a negative
potential. These circuits overcome any difficulties experienced in selection when the user is statically
charged due to a dry atmosphere and carpeting of a synthetic fibre material. Problems in selection associated
with a low impedance ground path such as when the user is in contact with a metal radiator can be solved by
ensuring that devices have their inputs conditioned towards ground when they are being selected.
69
• vss
240V 50Hz
~
$~
240V 50Hz
~
3
$
• VOO,VSS
REVERSED FOR
ML 237, ML239
TOUCH
CONTACTS
VSS
01
IN4005
10M
R4
150K
TOUCH
CONTACTS
R2
1K2
t DIODE REVERSED
FOR ML237, ML2l8
NEON
• VDD
lal
• VDD
R1
2K2
lal
Ibl
Fig. 4 Touch plate components.
• NOT REQUIRED
WITH 'LOW REVERSE
LEAKAGE LED
Ibl
VDD
Fig. 5 Neon and LED circuit arrangement.
Channel Indication Using Neons
Miniature wire ended neons can easily be used as channel indicators. The ML230 series incorporates low
impedance current driving elements operating on the channel selection inputs. This means that the outputs
to the tuning voltage presets need be used for any other function. This isolation gives better tuning stability.
Fig.5(a) shows how easily a neon such as Hivac 3L type can be incorporated into a mains voltage touch
sensing arrangement similar to that shown in Fig.4(b). The direction of the diode will be reversed for negative
touch sensing circuits ML237 and ML239. Neon indicators are cheap and only demand a current ofO.3mA to
1mA to fully illuminate a miniature wire ended type. They do however, require a high voltage supply in orderto
strike satisfactorily. To add a neon indicator to the touch circuit shown in Fig.4(a) a supply of 150V and a
series resistor 0.7mA. When using neons with lower voltage touch sensing circuits care should be taken that
the neon striking does not degrade the touch sensitivity. A neon 'hold off' transistor may be required,
particularly with the ML237 and ML239 negative sensing circuits when low voltage touch sensing is used.
Such a circuit is shown in Fig.6. Immediately the input voltage falls below th!l threshold due to a finger
resistance across the touch contacts, a mute pulse is generated which turns on the BC546 transistor. With this
transistor on, the voltage across the neons is reduced to 33V and all neons are extinguished. After the mute
pulse the.BC546 transistor turns off and allows the new channel indicator to strike across the full103V supply.
The transistor switch thus ensures that all previous indicators are cleared and no leakage paths exist to
interfere with the new selection.
+.33V
+ 70V
330K
560K
47K
----,
100K
ML237
ML239
I
I
I
1K
560K
"
1K2
10M
39K
-33V=-.j>-----t============t-----
8200
OV
MUTE LINE
Fig. 6 Mute used to 'hold off' neons
IML237, ML239).
70
Fig. 7 Low voltage sensing with improved
s'ensitivity.
LED Channel Indicators
LEOs can easily be used as channel indicators provided that the maximum drive current is not exceeded. As
can be seen from the data sheets the 'ON' resistance of all ML230 series varicap outputs is less than 1000hms
at a current of 10mA. The input 'ON' resistance is a maximum or 2500hms at a current of 10mA except when
using the ML237 and ML239when the maximum current is 2mA. Thus LED's can bedriven at 100r 12mA from
the outputs or a current of 4 or 8mA may be used from the input pins in the case of the ML231, ML232, ML236
and ML238.
Fig. 7 shows a low voltage sensing circuit with LED indicators. The LED current is defined by the 1.2K and
8200hm resistor as about 10mA. An offset voltage is fed from 9200hm resistor via the 10M leakage resistor to
the input. This offset voltages of 11.8V in the case of Fig. 7 increases the touch sensitivity to 20Mohms. The
diodes supplement the reverse characteristics of the LED's. The 1k resistor sets a voltage of 0.6 V SS on this
diode, to reverse bias it when no channel is selected. This is important at turn or when the ML236 is cascaded,
because LED leakage could cause spurious selection.
The difficulty in using the ML237 or ML239 inputs to drive higher current indicators is due to the fact that the
MaS transistors used as source followers given an appreciable voltage drop. This could lead to the channel
selection threshold being exceeded and so channel selection would not be stable. Fig.8 shows an example of
such an input characteristic. More current than the guaranteed 2mA may be sunk by the input, but as the
voltage increases towards the threshold, stable selection becomes more difficult to maintain. The load lines
shown given an indication of the series resistance required, but is should be remembered that Fig. 8 is only an
example and not typical of all devices. Also, the threshold voltage specification is 0.4 to 0.6(V SS-V DO),
ANY CONVENIENT
SUITABLE
POSITIVE SUPPLY
DROPPER
• 33V REGULATOR
180
RESISTOR
33.7 j-{:=-.---!
4K
5K
11N
6K
(mAl
VARICAP
'VOLTAGE
TO TUNER
OL-________- ,__~L-~~__~~~~~~~~.
o
10
VTH
20 VIN {W.R.T. VDDI30
VSS
680K
Fig. 8 Example input characteristic
(ML237).
Fig. 9 Varicap Supply and Selection.
Varicap voltage switches
All ML230 series devices are guaranteed to have an output resistance of less than 1000hm for their varicap
output switches. This means that excellent regulation can be maintained for the varicap output voltage. As
mentioned previously the varicap supply, V SS, is brought out to a different pin Fig. 9 shows the simplest
arrangement that allows different tuning voltages to be present using the 1OOK variable potentiometers. Only
one MaS switch is shown and only 3 channels, but 6, 8 or more channels can be accommodated. However
many channels are used only one MaS switch wil be 'ON' at any time. The diodes allow the potentiometer
settings to be independent of each other. One idea for temperature compensation is shown, but a number of
systems can be used to compensate for not only the varicap drift and the varicap supply stability but also the
0.5V/o C or so change in voltage across the MaS switch and the 2.3V/ 0 C of the diodes. Forward biased
diodes, zener diodes and thermistors may all be utilised for best temperature stability.
71
STEPIIP,--------------------------,
100K
Fig. 10 24 channel touch selector with stepping facility.
6 PROGRAMS 1 x ML232
8 PROGRAMS 1 x ML238
12 PROGRAMS 2 x ML236
18 PROGRAMS 2 x ML236
r---r---C:~c:----1 + 200V
220K
18K
'OIlA.
.33V
TO TUNER
I-'---,.--<=:r-'--c:::>-t-- VAR I CAP
CONTROL
rC:::J-+-t-t-t--I ML230 I--Co..rC:::J-+--t-~
SERIES
i--cLf::)
"--', '100
820K
VDD
-:, STEP
:
INPUT .... ,
LI
Fig. 11 ML230 Series Minimum
Components,
Fig. 12 ML2398 driven from single high
voltage DC supply.
A universal application
Appendix 1 contains a printed wiring layout, circuit configuration and component details for a positive or
negative touch selection application using LED's or neons respectively. Most of the component details have
been covered previously and either circuit can be easily adapted for other slightly different requirements.
Included in the ML236 data sheet is an application circuit for a 12 channel touch selector using 2 devices.
Fig.10 clearly illustrates how any number of ML236 devices may be cascaded, diodes will be needed if more
than 2 devices are. cascaded.
Fig.11 incorporates an AFC defeat function when momentary action push switches are used. Very few
components are needed for this configuration which offers all the main facilities.
The circuit in Fig.12 only requires a single supply for neon, chip and varicaps. A shunt regulator controlled
from the varicap zener feeds the chip and the varicap tuning voltage out is temperature compensated.
ML238 application circuit
It will be seen from Appendix 1 that the ML238 circuit uses a low voltage (33V) touch selection supply with
improved sensitivity circuitry. The mute time constant capacitor of 22nF gives a mute time of about 18ms at a
V SS of 33V. When a stepping input applied the mute time is increased by the width of the stepping pulse.
Some temperature compensation is afforded by the diode connecting the lower end of the preset
potentiometers to chassis. An added facility not previously mentioned is the band selection circuitry for
72
multi-tuner arrangements. The set of 3 way switches an ow band I III IV N to be selected automatically for any
channel via the 3 emitter followers.
ML239 application
Appendix 1 gain shows a low voltage touch selection supply for this device. A new selection is made when an
input becomes more negative (towards chassis) and falls below the input threshold. Thus this device in this
application will not only switch when the user has a high (negative) static charge, but will also switch
satisfactorily when the user is at ground potential (due to contact with a central heating radiator say).
A 150V DC supply is used forthe high intensity neons because such neons have a high striking voltage. A high
voltage transistor, turned on by the mute output is ued to turn off all indicators during a channel change. This
transistor has to withstand the full neon striking voltage and also survive if no neon is on, during start up for
instance. The BC447 transistor used has an 80V BV CBO and BV CEO • Also it is used with an 18k base-emitter
resistor. The touch sensitivity is not quite as good as the previous application and so the touch plate resistors
are kept low at 560k, the minimum allowable by the safety limit.
Appendix 1
.15 40V TO 200V
WITH SUITABLE RESISTORS
If
SOUND
AFC
MUTE • DEFEAT
OK JL
mJ n~:l·
Im
vss
1~"~~ft6'
: ,,:;;j-<_.
';~~~~
..
1K
2M7
1 ~~vsvl.
0 ~~r--- ~~
I'
ML23B
·
··
f~~, ,_,
-,J"
1K2
n
IYI Yl
B200
nn
BANDS I III VIIV
Appendix I. Fig. 1.
• 150V
560K
47n
~I-
47l<
~X
,- JJ]1
t :1BK
]BC4
".
VDD
OV
220K
~~~~ _ oJ oJ -TQUCH
PLATES
47K
~
K5
m,
VARICA P
CONTR OL
~~
,-----
-,
,
,
,
"
"
100K
~
"
,
,
"
.,
"
, Ml239 "
"
"
-"
"l-
33n
"h
ff"~
n
.12V
_oJ
~od_Qd
I
I
I I I
33K,r.;:
.'!:> 'r.;:
~{r.:;J
_... _--
Appendix I. Fig. 2.
I~.
BANDS I II
VIIV
73
8200
-=-
GROUND
BAND1 - TO VARICAP - BANDIV -
=
+12V
lBANDll1
\10M(~
~
:§:
--
+,33V,
-=-_
~.l
_-
STEP INPUT
CLEAR INPUT - -
___
.-----~--_--
-
MUTEOUTPUT=
~.
N
lJJ
OJ
~T _
~o~ bD• ~
-=--~-=- 1k
-=r
L
ill
...
r
33k
1mS
I ..
82mm
Appendix I. Fig, 3,
-=--==-)
-=<==J-@
560k
~
~20k'"
--+c)-®
.....c- ® 1MH
--<><--<
GROUND--·
BAND 1
TOVARICAP=
BAND IV
+12V
,BAND III - - -
=
-------~)
--<}--
...po--
+,33V - STEP INPUT
CLEAR INPUT
I
-
-«>-
.....q.:..
o-e-o-e--
~®
~
--"'>-
~560k
c:=,=j T
MUTE OUTPUT =
+150V
--
~
@
..J
Appendix 1, F'Ig,4,
______________ ,A,~ppend~/, F0,
74
~
L
Appendix I.
Fig. 6
Appendix 2: Pin Connection Diagrams
SENSE INPUTS
INDICATOR OUTPUTS
VARICAP
OUTPUTS
SENSE INPUTS
VARICAP
OUTPUTS
INDICATOR OUTPUTS
ML2318
CLEAR INPUT
VOO
VSV
SERIAL IN
reo,,"
INPUT CH 1
Voo
OUTPUT CH 1
SENSE
INPUTS
INPUT CH 2
INPUT CH 3
OUTPUT CH 2
NEON
OUTPUTS
INPUT CH 4
OUTPUT CH 3
INPUT CH 5
OUTPUT CH 4
INPUT CH 6
OUTPUT CH 5
STEP INPUT
OUTPUT CH 6
INPUT CH 1
OUTPUT CH 2
VARICAP
OUTPUTS
ML2328
INPUT CH 2
l
OUTPUT CH 3
INPUT CH 3
OUTPUT CH 4
INPUT CH 4
OUTPUT CH 5
INPUT CH 5
OUTPUT CH 6
INPUT CH 6
MUTE SWITCH 1
SENSE
INPUTS
INDICATOR
OUTPUTS
NO CONNECTION
MUTE SENSE INPUT
Vss
MUTE SWITCH 2
STEP INPUT
RESET OUTPUT
SERIAL OUTPUT
MUTE TIMING
CONTROL
VARICAP
OUTPUTS
MUTE OUTPUT
Vss
VSV
ML2378
ML2368
75
NO CONNECTION
SENSE
INPUTS
INDICATOR
OUTPUTS
Voo
OUTPUT CH 1
INPUT CH 1
INPUT
CH 2
OUTPUT CH 2
INPUT
CH 2
OUTPUT CH
2
INPUT
CH 3
OUTPUT CH 3
INPUT CH 3
OUTPUT CH
3
INPUT
CH ,
OUTPUT CH
t.
INPUT
CH 5
OUTPUT
INPUT
CH 6
INPUT
CH 7
OUTPUT
INPUT
INPUT
CH ,
OUTPUT CH
NEON
OUTPUTS
INPUT
CH 5
OUTPUT
OUTPUT CH 6
INPUT
CH 6
OUTPUT CH 6
CH 7
INPUT
CH 7
OUTPUT
CH 7
CH 8
OUTPUT
CH 8
t.
CH 5
CH B
VARICAP
OUTPUTS
INPUT
STE P INPUT
MUTE OUTPUT
STEP INPUT
MUTE TIMING
CONTROL
CLEAR INPUT
MUTE TIMING
CONTROL
VSV
ML2388
OUTPUT CH 1
SENSE
INPUTS
OUTPUT
CH 8
VSS
76
NO CONNECTION
Voo
INPUT CH 1
CH 5
MUTE OUTPUT
CLEAR INPUT
VSV
VSS
ML2398
VARICAP
OUTPUTS
6. REMOTE CONTROL
USING PPM
77
78
Introduction
Plessey Semiconductors have developed and produced two integrated circuits that when combined give on e
of the most flexible remote control systems on the market. The SL490 is a pulse-transmitting remote
controller, for use in conjunction with the ML920 receiver.
Methods of control can be achieved by cable, sound, ultrasonic, visible light, infra-red or radio frequency.
On a television set, it is possible to control the Brightness, Volume and Color in 32 steps from minimum to
maximum. In addition, facilities for Sound Mute, Color Kill and Normalise, as well as a number of other options
which will be fully described later, are incorporated within the system. The system can be used with Television
having 8,10,12,16 or 20 programme selections. If more than 20 selections are needed, the system is easily
expanded.
Commands are transmitted by codes via a pulse position modulated signal. The SL490 can give a modulated
carrier frequency from the on-chip oscillator. This on-chip oscillator, used for carrier generation, is selectable
so that pulses with or without a carrier frequency may be transmitted.
The Pulse Width/Modulation Rate is variable, and PPM results in:(i) An economy of Channel Width
(ii) A greater number of Commands Binary Codes, transmitted in a Pulse Position Modulated Signal help in
ensuring that incorrect signals do not operate the receiver. 5 bits of information contained within 6 pulses are
transmitted and when detected by the receiver are checked. Pulses must be of the correct pulse width, in the
correct position, the gap between words must be as designated, and finally, two identical words must be
received before the receiver is allowed to action the sinal. Consequently this system is virtually immune to
incorrect signals.
As current is conducted only when a contact is made by a key switch, negligable power is consumed from the
battery in the transmitter, thus ensuring that battery life is nearly as long as shelf life.
A whole series of domestic appliances may be controlled by just one transmitter. For example, since the
remote control system can be used for Television, Radio/Tuner, Tape/Recorder Decks. Garage Doors etc.,
then with just one transmitter the following can be controlled remotely:(i)
(ii)
(iii)
(iv)
the garage doors may be opened.
a porch light may be switched on
a radio, tape recorder or television may be switched on and the desired programme selected.
cooker hotplates or oven setting may be adjusted.
I9vI
BATTERY
L
PP3
...J
4x8
• __ ~~TRASONIC
KEY
MATRIX
NETWORK
L--J
q""
tl~ED ~
~~
Fig. 1.
~~~---:
FI~~ER
,-_...1.-_--',
Plessey Remote Control System Block Diagram
79
Other Possibilities
(1) An automatic telephone answering machine can itself be commanded to relay all its messages over the
telephone, instead of having to manually play-back the telephone messages.
(2)
The Remote Control of Toys and Models.
(3) Industrial Control e.g. may be used to trigger, interrogate, and transmit back information from a substation to the Main station, so that data can be analysed and appropriate actions carried out.
In general, all systems that have in the past relied on some method of manual triggering such that infromation,
data etc. can be recorded and perhaps appropriately actioned, can noe be remotely triggered and remotely
actioned.
The Transmitter Unit
The SL490 though initially designed with TV remote control in mind may be used whenever a compact pulse
coded digital transmission system can be realised. A basic 5-bit code is used giving 32 code words which can
be modulated as pulse position modulation (ppm) onto a single carrier frequency or transmitted as baseband
pulse position modulation. Fig.1 shows how an ultrasonic or infra-red link may be used to control 3 analogue
settings, select up to 20 channels and give 6 other control functions by using an SL490 ppm transmitter and a
ML920 ppm receiver. The SL490 could equally well be used to drive a cable link or a radio link.
Only single pole switches are needed in the key matrix and fairly high 'on' switch resistance may be tolerated.
The transmitter has a very low standby current (leakage only), and a transmission is economical on power due
to the design and low duty cycle of pulses fed to the load. An ultrasonic transducer may be fed directly using
only 2 resistors and 3 capacitors external to the device. Thus, small battery, ahnd held, portable operation is
easily implemented and low cost ultrasonic transducers may be used at their natural resonant frequency.
For infra-red operation, a 2 or 3 transistor amplifier is used to feed very narrow high current pulses to a gallium
arsenide, infra-red emitting diodes, such as the Plessey GAL32. If a higher output is required, 3 or 4 GAL32
diodes can be used in parallel. The pulse nature of the signal allows the diode emitter to work at a higher light
output efficiency and the battery current to be reduced. Figs.2,3 and 4 show the output voltages waveforms
obtainable. Fig.2 shows a lower than normal carrier frequency compared to the pulse width. This is done for
clarity although the device would operate satisfactory with such timing.
'1'
'0'
_ _ TIME
Fig. 2.
3mS
27mS
Fig. 3.
80
18mS
PPM Output showing ultrasonic carrier frequency
54mS
Ultrasonic transmitter output
(For A '1' period of 18mS)
Fig. 4.
PPM output (Pin 2) with no c.arrier
The Receiver Amplifier
At the receiving end of the link, the system will require some sort of gain and bandwidth defining stages,
before the detected signal is fed to the ML920 receiver. Usually 2 or at the most 3 amplifier stages are sufficient
with some fairly simple active filtering, and in the case of the infra-red link, an infra-red filter, required before
the photo transistor. After filtering and amplifying the ultrasonic frequency, a simple diode detector may be
used. The detected PPM can then be fed to the ML920 via a buffer amplifier stage. Fig.S shows how an
ultrasonic frequency of 33KHZ to 43KHZ may be chosen to avoid the second and third harmonic of the TV line
output stage.
An inexpensive transducer may be chosen with its natural resonant frequency within this band, and driven at
its natural resonance which simplifies loading and improves power output. The actual bandwidth needed
about the carrier is approximately 10KHZ. The data rate may be chosen by considering the rate at which the
analogue outputs of the ML920 are required to step. If for example we require an analogue output to sweep its
full range (32 steps) in about 10 seconds, this requires one step every 300m sec or so, but because of the
receiver error checking code comparator, the transmitter word rate should be set to 1S0msec.
Referring to Fig.3, it will be seen that the code word period including the inter-word space is 162msec which
will give the required analogue change rate, full range in about 10 seconds. The only adjustment needed in the
receiver is to set the oscillator time constant, so that 20 time periods on the receiver monitor, (pin 9),
corresponds to a '0' interval of the incoming PPM (see Fig.6). The demodulator timing oscillator frequency
tolerances of up to 10% in both the transmitter and the receiver. This can be seen from the timing window
durations of Fig.6.
1st
t
AMPLITUDE
J)
TYPICAL ULTRASONIC
TRANSDUCER RESPONSE
...
,
3rd
\
1\
\
40
NARROW FREQUENCi---'
lOR PPM SYSTEM
I
'S'
15K625
31 K25
-
46K875
FREQUENCY
(Hz)
Fig. 5. Ultrasonic transducer reponse with line frequency
10
16
30
RESET
60
TIME PERIODS (PIN 9) - -
Fig. 6.
PPM Demodulator timing
and its harmonics
An infra-red link
For short range remote control, infra-red links have advantages over ultrasonic links-less multipath
interference, lower spurious radiation, less annoyance to humans and animals, a higher modulation rate
capability and more robust transducers. High efficiency infra-red light emitting diodes (LED) are relatively·
inexpensive and can incorporate both reflector and lens for a more concentrated beam light. Multichip
assemnlies are also becoming more common and these can take fairly high currents, LED's become more
efficient at higher currents, and pulse an d multiplex systems are common for display systems. Thus a PPM
system can be made to operate a LED at quite high outputs for small increase in battery current. Morethan one
LED may be connected in series at lower currents and in parallel at higher currents, and these emitters can
have different orientation of their axes if required.
On the receiver side, a photo diode or photo transistor can be used with an appropriate infra-red filter. Fig,7
shows how a photo detector response, although peaking in the near infra-red region, has good detection
properties at visible light wavelengths and into the ultra-violet. As the energy emitted from a gallium arsenide
LED is in the main a narrow band emission at 940nm, a correctly chosen filter will attenuate greatly most of the
interferring noise signals. Other noise sources which have large emissions in the infra-red e,g. a tungsten
filament lamp, can be rejected by carrier modulation of the infra-red link,
81
Both amplitude modulation and frequency modulation have been used, but neither have simplicity nor all the
advantages that a pulse system can offer in LED driving efficiency and economy of detection. Pulse Position
Modulation using a narrow pulsed high current drive to a gallium arsenide LED, enables a very good signal to
noise ratio to obtained at the demodulation. Only photo-detector saturation (in very bright sunlight for
example) or the very close proximity of a high output fluorescent gas discharge tube could cause the
reception to be interrupted.
SL490 - remote control receiver
General description
The SL490 ia an 18 pin, bipolar, remote control pulse transmitting monolithic circuit for use with the ML920
Receiver Single pole switches arranged in a 4 x 8 matrix or 12 keys (1 out of 4 and 1 out of 8) are encoded by the
device which then gives a modulated carrier frequency from an on-chip oscillator. A standby current of only
6uA or so is taken from a 9V supply by the device until any switch closure is detected. (A PP3 battery can have
a battery life of about two years in this system). The modulated output can drive an ultrasonic transducer
directly at its natural resonant frequency, enabling inexpensive crystals to be used. A 5 bit pulse position
modulated signal is used giving 32 basic commands. These commands could be used in a TV remote control
system to select 20 programs, control 3 analogue functions and provide 6 additional switching functions.
Apart from the battery, switch, matrix and transducer, only 3 capacitors and 2 resistors are needed externally .
. A single RC selects carrier options and defines frequency. The other RC defines modulation rate. Output
capability is direct ultrasonic transducer feed, and complimentary outputs with or without active pull ups.
Continuous or pulsed visual indication can be driven directly from pin 2. Carrier oscillator may be disabled for
pulsed operation of infra-red. More than one set of 32 commands may be utilised by changing modulation
rate/carrier frequency.
Despite the comprehensive range of facilities offered by this remote control system, the SL490 makes the
transmitter a very simple unit. Fig. 8 outlines the block diagram of the transmitter.
100
TRANSMISSION
(%)
SILICON
PHOTODETECTOR
80
60
40
20
0.3
0.4
0.5
0.6
0.7
0.8
o.g
WAVELENGTH (urn)
Fig. 7.
82
Optical Response Characteristics
1.0
1.1
1.2
Circuit operation
The device transmits a code word as a group of 6 pulses. Each of the five intervals between these pulses may
take up 2 possible values, a short interval corresponding to a '1' OR A LONG INTERVAL CORRESPONDING
l' or a long interval corresponding
to a '0'. Fig.3 shows the timing relationship between pulses '1', '0' and'S', the space or synchronisation gap
between words. The ratio of the intervals representing '1','0' and'S' is 2:3:6 and is fixed by the device. In
addition the width of the pulse is about 1/6th of '1' interval or 1/3:2 on the above ratio scale. Thus 32 different
codewords may be transmitted by the 5 bit code.
A particular codeword is selected by switching one out of eight current sources to one out of four current
sinks (one of these current sinks is 0 Volts). All decoding is done by the integrated circuit, (see Fig.1 0). The
circuit draws only about 6uA from the supply until a switch closure is detected. Power is then applied to the
whole circuit. The appropriate PPM code is then generated repeatedly until the switch is released, whence,
the device reverts to standby, after the codeword being transmitted is completed.
3
~D
TIMING
GEN
SWITCH
MATRIX
MONITOR
CURRENT
CODE L--.-r---,
REGIST
ONI
STANDBY
COUNTER
L-.J
SWITCH
MATRIX
CURRENT
SINKS
POWER CLEAR
CARRIER
18
~
OV
Fig. 8.
TIMECONST.
NORMALISE
14
AND
LOGIC
.STEP PRO,
STEP
DECODER
ON
11
RECALL 12.
AFC-13·
15
TIME CaNST.
Transmitter SL490 Block Diagram
EDC BABABABA
00
000
01
10
~ r[;"~
"
001
100K
OlD
0"
r,og~
100
lDI
\10
\II
l-
SL490
'---
'---
9V
k
ill
lt~
I
16 171819 20
1
-.;.
"-'>
Fig. 9.
Remote Control Receiver ML920 Block Diagram
~~PL101
I!-t-I---
6r~~1-
100~~
COLOR KILL
lOOK
1K
100K
}OOK
.
J. BC547
ov
Fig. 10.
Ultrasonic Transmitter Unit
83
ML920 - remote control receiver
General description
The ML920 ,is a 24 pin PMOS/LSI monolithic circuit, designed to decode the 32 possible 5 bit codes
transmitted by the SL490. It functions as a remote control receiver of pulse position modulated signals. After
demodulation, verification and comparison of 2 consecutive codewords, the incoming pulse position
modulated signal is decoded to give 20 channels, 3 analogue controls plus 6 other control functions. It
requires a supply of about 17 Volts and 12mA. Fig.9 outlines the block diagram of the Receiver.
Circuit Operation
The ML920 operates on a timescale fixed by the on-chip oscillator and an external Rand Ctime constant that
defines its frequency. A counter is reset whenever an input pulse is received (see Fig.6). The counter defines
timing windows for the following pulse. After a pulse is received the input is disabled until a count of 10. This is
to prohibit any possibilities of pulse echoes of multipath reflections upsetting the correct transmission. If a
pulse is received after a count of 10 has been attained, it will be accepted as a '1', a '0' or an'S' ('S' is the
synchronisation interval or interword space). If a space is received, then a check is made to ensure that 6
pulses have previously been received. If no pulse has been received when the counter reaches 60, then a
general reset takes place, and the start of a new codeword is awaited. Only when two successive codewords
have been correctly received and a comparison check to prove that the two codewords are identical, is the
infromation passed to the decoder to be acted upon.
The ML920 has 3 Digital-Analogue converters on its chip. Its outputs are in the form of current sinks which
have 32 current levels from 0 to about 1mAo In Television, this eliminates some interface circuitry and allows
this device to control circuits such as the TBA120S and the TBA560. Hence, direct controls of the Volume,
Brightness and Color of the set is possible. An Up/Down counter is incorporated into the 5 bit data highway
and this allows channel, volume, brightness or color words to be read, incremented and re-written into their
respective stores. If 'color' is zero then 'color kill' is automatically generated. The circuit also has sound mute
which turns the sound down to zero instantly, thus avoiding the ramping down of the sound through a 32 step
volume control, as it has a slow rate of change to allow fine control. When the mute button is pressed a second
time, the television reverts to its original volume. The ON/STANDBY output switches the TV on from the
standby condition or vice-versa.
ML920 Pin Functions
Negative Logic:
'0' is OV (V ss) 'I' is - 17V (V DD)
Pin
Name
Function
3
VDD
-17V power
su~ply
4
VSS
OV power supply
5
ON/STANDBY liP
A '1' on this pin will toggle pin 11 (ON O/P), generate RECALL
and AFC VOLUME, BRIGHTNESS and COLOR, reset MUTE
and set channel code 00000.
6
NORMALISE liP
A '1' will normalise the VOLUME, BRIGHTNESS and COLOR
outputs A RECALL signal is generated and MUTE is reset.
7
PROGRAM STEP
The program code will step up by 1 as long as this pin is held at
logic '1 '. The time period between steps is defined by an RC
constant attached to pin 15. On reaching 20 the next step
returns to 1. On output is set to ON, and AFC is generated. If the
TV goes from Standby to ON, RECALL is generated and
VOLUME, BRIGHTNESS and COLOR are normalised. If
VOLUME is 0, MUTE is reset.
8
OSC. TIME
CONSTANT
An RC time constant is formed for the clock timing be
connecting external components one resistor and one
capacitor, to this pin. Adjusted so that period of outputs on pin 9
is 1/20 of '0' interval of incoming ppm. by
9
OSCILLATOR
MONITOR
This output is a division of two of the oscillator, and is available
for testing and setting purpose
84
10
PPM liP
The output of the front end amplifier is connected here such that
the signal is in the form of positive pulses seperated by time
periods whose length define the data. With no signal PPM input
is at a logic 1.
11
ON OIP
Open drain output. Logic 1 denotes TV set ON: Logic '0' TV set
standby. Set to 1 when program number changes
Set to 0 power clear or by Transmitter selected 'Standby'.
Toggle to opposite state by manual ONISTANDBY control
12
RECALL OIP
Open drain output A '1' may be used to trigger an on-screen
display. A static output is generated by the manual controls
ONISTANDBY and NORMAL.
A pulse is generated by any channel change if the circuit
switches to 'ON' at the time, and by RECALL and NORMALISE
commands from the transmitter.
13
AFC OIP
Open drain output. Logic 1 can inhibit the tuner AFC
A static output is generated by manual ONISTANDBY control.
A pulse is generated by any program number change.
14
POWER CLEAR
A capacitor and resistor connected here define the time delay
for the power clear circuit which normalises all D-A outputs
etc.
15
PROGRAM STEP
TIME CONSTANT
An R-C time constant defines the time period between
increments of the channel when stepping.
16-20
PROGRAM
5 Outputs encode 20 program numbers in binary code
Program 1 is
Program 20 is
E DC BA
0 0 0 0 0
1 0 0 1 1
E is first and A is last in the PPM pulse train.
Program 1 is set when ON goes to a '1 '.
21,23,1
VOLUME
BRIGHTNESS
COLOR
These three outputs are from three 5 bit current mirror DIA
converters. They are referenced to the current drawn from pin
24, Iref, and give 32 steps, Iretl8 per step, from 0 to 31/81ref. The
outputs will be set to 12/8 Iref by the NORMALISE liP the
mormalise code from the transmitter or when the ON output
goes to a '1'.
22
MUTE OIP
This will change state (toggle) on reception of a mute command
but if VOLUME OIP is zero MUTE OIP is held at '0'.
24
DIA REFERENCE
A current drain Iref, set by a single external resistor will fix the
nominal step of the DIA outputs to Iretl8.
2
COLOR KILL
This OIP gives a logic '0' when the COLOR DIA output is zero.
Applications
Ultrasonic Transmitter
As previously mentioned the SL490 PPM transmitter and ML920 PPM receiver can be used whenever a binary
digital channel exists to control both digital and analogue functions. Fig.10 shows how an additional NPN
transistor (BC547) may be used to drive a visible light LED is required. Two PNP transistors (BC557) may also
be added as shown as active 'pull ups' to increase the power fed to the ultrasonic transducer at the expense of
a slight increase in battery current consumption. Without these, the output current is limited to about 5mA by
internal pull up resistors, but even with the transducer directly powered from pins 2 and 3, adequate load
power is obtained by the 18V effective output swing.
The modulation rate of the PPM signal is set by the CR network on pin 16. With the 220nF capacitor shown, a
variable resistor set at 50Kohms should give a PPM speed such that the word rate is 150mS, but almost any
85
desired rate can be selected if required. The CR network on pin 18similarly sets the desired carrier frequency.
In this particular application the 1.5nF capacitor and the 22Kohms resistor are used. to set the carrier
frequency to the natural resonance of the transducer, about 38KHZ. By choosing a suitable capacitor and
trimming resistor, a wide range of carrier frequencies (0 to 200KHZ) are possible.
Ultrasonic Receiver
Before the received Ultrasonic signal can be detected and 'fed to the ML920 PPM demodulator, it must be
amplified. Some frequency selectivity is also desirable and this can be achieved by an operational amplifier,
active filter stage. Fig.11 shows how an SL748 can be used as the first amplifier stage. Some lower output
transducers may require an additional single transistor amplifier stage before this. The amplified signal is
detected by the NPN transistor (BC547) and after smoothing, is fed to the interface amplifier. The input of this
amplifier is biased so that a threshold is set up just above the noise level. The output is thus reasonably noise
free and sufficient amplitude to drive the ML920 directly into pin 10. This receiver together with the transmitter
has been used to give a working range of 6m without active pull ups and 8m with active pull ups although this
does depend on transducer efficiency. The word rate used is about 6 per second giving a command rate of 1
receiver command every 300mS. The circuit and component layout is shown in Fig.14 a(1d Fig.15.
Infra-red Transmitter
For infra-red transmitter unit, the SL490 is easily madeto give out a carrier frequency, or converted so that the
output will consist of narrow DC pulses. If no carrier frequency is needed for the PPM output then no capacitor
is needed on pin 18 and resistor value should be reduced to 2.2Kohms. A narrow current pulse is derived from
pin 3 shown in Fig.12 and this is used to drive the LED array by a PNP-NPN configuration, (in this instance the
NPN transistor is a Darlington pair). The arrangement gives up to 10Amps. current pulses and can be used as
extreme ranges with a sensitive receiver.
Battery consumption is only increased by 50% because of the low duty cycle load current pulse: pulse width
may be reduced to less than 15uS, but phototransistor response may be decreased for narrower infra-red
pulses. Usually sufficient power output will be available when a simple NPN output configuration with 1 to 3
LED's connected in series. Parallel connection is only needed at higher currents when adequate current
sharing takes place between LED's of the same type. The current pulse is drawn from 470uF capacitor which
should not have excessive inductance or long connections to the load. In addition if a visible light is needed to
indicate that the transmitter is operating, a red LED may be connected directly to pin 2, the other output pin.
(unused in this application). This is also shown in Fig.12.
17V
1M
10K
lOOK
3p9
BC547
SL748
22n
1M
1M
3K3
l20p
120p
-j f--..----l
lOOK
47K
1
ul
lK
__
~
______
~
______
~
__________-4__-4__
Fig. 11.
86
~----------+-~---OV
Ultrasonic Receive Amplifier
39p
Infr-Red Receiver
The photodetector should have a filter with
adequate cutoff towards the visible light region.
A Kodak type 87C is suitable and allows a high
gain, operational amplifier, active filter stage to
give very good sensitivity (Fig.13 shows such a
configuration). The circuit should be well
screened from electrical noise. I ndeed the
screen can be extended over the photodetector
lens as an open mesh. The BPW34 photodiode
gives a good response to weak signals down to a
1OuS pulse width. The SL748 in Fig.13 filters the
detected infra-red signal and amplifies the
pulse, feeding it to a CMOS 2 input and gate.
The first gate is biased in class A and the other 2
form a monostable. Some sensitivity control and
monostable threshold variation are achieved by
a simple 1M ohm potentiometer. This gives a
very clean pulse at the output which is transistor
buffered and fed to the ML920 PPM receiver.
The ultimate range of the transmitter receiver
was found to be 27 m. More usual ranges may be
dealt with by using only a single output NPN
transistor and transmitter LED, where the range
was found to be about 8 m. The word time used
was 75ms, twice the speed of the ultrasonic link.
The layout and component positions can be
seen in Fig.16 and Fig.17.
10
11
OO~O~~~________~
00~1~~~________- ,
010
4701'
16V
1K
3n3
Fig. 12.
-
/' -SCREEN-
820
SA SA SA SA
ECtOO 0\
Infra-Red Transmitter
-"
17V
(
180D
I
I
I
6K8
SL748
87c
15p
+
I
FILTER
(OR SIMILAR)
I
BC547
680p
330K
1M
1M
\
\
/
Fig. 13.
OV
Infra-Red Receiver for PPM
87
The ML920 Receiver
Very little is needed externally to this device, there being a high degree of integration on the chip. Pull up load
resistors of about 50K ohms are required, however, on all digital outputs except the oscillator monitor. Fig.18
shows this and the other basic requirements. The whole receiver timing is set by a single RC time constant on
pin 8. Final adjustment is achieved by monitoring pin 9 which gives a buffered, divide by 2 of the main
oscillator. The correct setting will be when 20 complete cycles on pin 9 occur for a '0' interval in tne received
PPM signal. Two other time constants may be needed: a'power start up RC on pin 14 which clears and
intialises the chip when its supply is switched on and a second time constant on pin 15 may be needed if the
program step is used. This defines the stepping rate.
The analogue outputs will need a current mirror reference on pin 24 (about 0.35mA) and 5 bit D/A converter
outputs themselves will each need a current sink for the 0 to 1.4mA or so to which they may be set.
For maximum linearity these current sinks should not allow their voltage to exceed 5V or so (3.9K ohms
maximum), but this may be increased to 10V if 10% linearity can be tolerated. The 3 manually controlled local
inputs are shown in Fig.18 as simple switched resistor pull ups. Some debounce may be needed in extreme
cases.
BC547
'Y .
~
1K
100K
Y ~
-()
~
lOOK
72mm
m
BC557
;gk
100K~ +..:
~.
~
2k
\.:-It.22~
f.J.
¥OOK;
BC557
•
..
• . '. I
...
~
62mm
Fig. 14.
Ultrasonic Transmitter P.C.B. and Component Layout
1
50mm
I
TO PPM
INPUT OF
ML920
.....11----------
OV~L748 lOOk~ f 10k ~ ~~~~ ~ ~1kg
-
Fig. 15.
SL748.
0 '8y~QY '~~TY"'~q
'Q • y+~~O
£
.. -O-6-n-
'g"
BC547,.
I
,17-L
88
•
.135mm
39 f lOOk
P
0 1u
10k
~
0.
I ~~*
..
3.9pf
Ultrasonic Receiver Amplifier P.C.B. and Component Layout
Additional Facilities
Up to 20 channels may be set, selected individually and stepped sequentially. If less than 20 channels are
needed then 6,8,10,12 and 16 are readily catered for. 10 channels may be utilised with no modifications,
instead of the latched output E,O,C,B,A, being decoded, the least significant bit, A, is ignored. When stepping,
a double channel step is needed to get to the next used channel. If stepping is not required any number of
channels may, of course, be used. Fig.19 allows fast 'end' around stepping of unused channels in a 16 or 8
channel system. When an unused program number is detected the step input is held low and the step time
constant is switched to 'very fast'. A similar circuit may be used to cater for complete stepping facilities with 12
or 6 channels.
As previously mentioned the analogue outputs are current sources giving 32 steps of current in the range Oto
1.4mA. This may be controlled by the current mirror reference on pin 24. Greatest linearity is obtained if the
current sink resistor on the 0/ A outputs do not exceed 3.9K ohms giving a 0 to 5V control range. However, a 0
to 10V range may be obtained with higher resistor values if some reduction in linearity can be tolerated. The
simplest form of local asjustment of analogue control levels is to make the current sink resistor variable, but if
more sophistication is required then Fig.20 shows how an operational amplifier may be used. This circuit
enables both the range and the OC value of the control voltage at the output of the operational amplifier to be
set and operated by either the remote control or the local control.
If local push-switch control of the analogue functions is desired, then Fig.21 shows how an additional SL490
with few external components may be used. The output of this SL490 is 'teed' into the receiver PPM line at the
base of the buffer transistor. On/Standby, Normalise, Step, Mute and Recall are all now available as local
controls from push-switches which require no debounce via the local control transmitter.
One transmitter can be used to control more than one receiver. Fig.22 shows how a simple slider switch can
change the modulation rate of the PPM to control another 32 command set receiver. As long as the command
rates differ by more than 30%, no cross coupling should be experienced because of the high integrity of the
receiver PPM demodulator timing. Fig.22 also suggests how an MOS transistor 'memory' and 2 push switches
may replace the 2 position switch.
In some cases a fourth analogue control output may be required from the receiver and it can beseen in Fig.23
how this might be achieved with the addition of some logic elements and a 0/A ladder network. 16 channel
selections are available, freeing 4 commands for other uses. Because of commands becoming 'mixed' it is
recommended that the step facility is not used in configurations where additional commands have been
incorporated. This simplifies decoding circuitry greatly.
72mm
62mm
Fig. 16.
Infra-red Transmitter p.e.B and Component Layout
89
1
44mm
1
4.~----------------105mm ----------------~~~
r
}2~.:" ~F~~:lt~~ omv+~
OV -TsC547
TO PPM
INPUT OF
ML920
_
n
6k8
-17V
+
LINE
OSC
I
~
LUMA
AMP
DELAY
LINE
INFRA·RED
PREAMP
IDENT&
ACC
DETECTOR
TDA2560
CHROMA]
AMP
i""
PHASE
DETECTOR
I
SUBCARRIER
OSC
~------::z.---.-4f-J
I
I
.1
.l
~
1
I
~
G-Y
COLOUR
DEMOD
~
R
MATRIX
I tEl
'---TDA2532 ----
PAL
SWITCH
J'90
J'
SYNC
SEPARATOR
AGC
GENERATOR
. BCD TO
VARICAP
DECODE
SOUND
IF
AMPLIFIER
TDA2593
J
REMOTE
CONTROL
TRANSMITIER
H
TDA2522
I
Jl!!l
mm'
INTEGRATED CIRCUITS FOR TV
'<
:nt.o
I
:::T1011
:T1111
:::T1112
:::T1116
::T1117
:::T1119
:::T1124
~
AFC
GENERATOR
, . - - ~~~:~~-
~
TUNER
IF
PREAMP
1
:::T1125
:::T1132
:::T1134
- ·1
51952
:;;P4020/1
'P4~40"
AGC
GENERATOR
H
TBA440N
TBA440P
r - - Sl1430----.
SOUND
IF
AMPLIFIER
ill 1
IF
AMPLIFIER
'- ~:~:~ oJ
DETECTOR
; - - TBA920S --...
I
t
SW170
SW171
SWl72
SWl73
SYNC
SEPARATOR
h
H
I
FRAME
SYNC
SEPARATOR
SW200
SW250
I
ML2J6B
Ml237B
ML2388
ML239B
PHASE
DETECTOR
I
INFRA·RED
PREAMP
I
M~20
r*-------:z:.---.~
CD
-.J
FRAME
OSC
l
~.
LINE
OSC
t--I
H>
~
l~l922
TBA560C
TDA2560
CHROMA
AMP
LUMA
AMP
ML928
M 929
J
DELAY
LINE
51
TBA540
IDENT&
ACC
REMOTE
• CONTROL
'rRANSMITIER
-;
SWl17J
,
. Ml232B
t-.
AGC
GENERATOR
SW180
REMOTE
CONTROL
RECEIVER
' - - - Ml23, B _ _
.
TBA950:2X
TDA2590/1 / 3
..............
SW45D
TOUCH
SWITCH
AMPLIFIER
TBAaoo_
SW4QO
'----Sl470---'
~
DETECTOR
'-TOA440
.vvzt>u-
BCD TO
VARICAP
DECODE
"., K
TBA120S/UIT
TDA2541
1---1
1
T
SUBCARRIER
OSC
COLOUR
DEMOD
~
~
~
l a
all::!:
MATRIX
•
' - - - - TBAS30_
TDA2530
TOA2532
PAL
SWITCH
.190
SL491
TDA2522
TOA2523
~
nOAaoo - - - - J
R
Ilib..l
~
~
~
INTEGRATED CIRCUITS FOR TV FREQUENCY SYNTHESIS
SP4020/Z1
SP4040/41
CT1011
r - SL9S2 --.,
LOCAL
OSC
....
J.... >
, - - - CT'O'O - - . .
FIXED
DIVIDER
en010
, - - - CT,O" ----.,
2 MOOULUS
DIVIDER
I-~
t-~ H
CT1112
CT1116
CT1132
, . - - cn" 9 _ _
VARIABLE
DIVIDER
-1-1
TUNING
MEMORY
PROGRAM
DISPLAY
1
ACTIVE
FILTER
AND
BAND SWITCH
I
I
PHASE
DETECTOR
DIVIDER
CONTROL
I
I
TUNING
CONTROL
I
I
'--cn'2. ----'
' - - - CT"17----'
CT1125
CT1134
£
CRYSTAL
OSCILLATOR
~
~
FIXED
DIVIDER
Bioi
:0101
USER
CONTROLS
7. TECHNICAL
DATA
99
100
.~!
CT2010
1 GHz ~ 3801400 PRESCALER
The CT2010 is a 380/400 two modulus divider which
will operate at frequencies between 80 MHz and 1GHz. The
device is the prescaler used in the Plessey Key Frequency
Synthesis Tuning System.
The input is terminated by a nominal 50 ohms and
should be AC coupled to the signal source. The reference
pin should be AC decoupled. The decoupling should be
effective over the full operating frequency range.
The divider contains a fixed divide by 20 followed by a
divide by 19/20. The divide by 19/20 divides by 20 when no
control pulses are applied to the control input. The divide
by 19/20 will divide by 19 once for every positive going
edge applied to the control pin. The control input edge is
latched and synchronised sothat the following output cycle,
commencing with a negative edge, is produced by 380 in·
put cycles to the whole divider stage, rather than 400. This
means that the device is highly tolerant of delay in the con·
trolloop and distortion of the control waveform.
To ensure that there is an output cycle produced by 380
input cycles for every control pulse, the rate of control
pulses should not exceed half the output frequency. (See
timing diagrams.)
The output source impedance is nominally 1000hms.
The output swing is nominally 300mV and swings down
from the positive supply.
ABSOLUTE MAXIMUM RATINGS
Supply voltage, Vce
UHF input voltage
Storage temperature
Operating ambient temperature
DIFFERENTIAL {
INPUTS
+7V
2.5V p.p
- 55°C to + 125°C
-10°C to +65°C
Vcc,~5V[ 1. '-"
8
MOOULUSCON1ROL [ 2 CT2010 7
UHf'VHfINPUi
NOT CONNECIED
OUTPUT [ 3
6
INPUT REfERENCE
GROU~m
5
GROUND
[ 4
DP8
Fig.1 Pin connections
FEATURES
•
I
On-chip Wideband Amplifier
•
High Input Sensitivity
•
High Input Impedance
•
low Output Radiation
•
•
Single Eel Output
5V logic level Control Input
•
Control Independent of Distortion and Delay
,
0"----+----'
-+---._
ov 65 _ _ _
Fig.2 CT2010 block diagram
101
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Test circuit: Fig.3
Vee = 5V, Tamb = 25°C
Characteristic
Pin
Operating voltage range
1
Supply current
Input voltage, 80 MHz
300MHz
V'N
500MHz
700MHz
1000MHz
Output voltage swing
1
8,6
8,6
8,6
8,6
8,6
3
3
Output impedance
Control input, high
4.5
90
17.5
17.5
17.5
17.5
17.5
240
2
2
2
2
2
low
pul5ewidth
Value
Typ.
Min.
Max.
Units
5.5
V
110
200
200
200
200
200
mA
mV
mV
mV
mV
mV
mV
300
100
Conditions
rrns, sine wave 50!!
rms, sine wave 50!!
rrns, sine wave 50!!
rms, sine wave 50!!
rrn5, sine wave 50!!
p.p, no load
!!
2/3 Vee
50
1/3Vee
-10
0.2
3
I'A
,..A
,..5
VHF lOCAL
~OSCILlATOR
FROM CT2012 OR
SIMILAR CONTROL
. 'f----."n"
',.
'"
~
'----'"
17m
50
""
'"
:bcr,':tc~
Inn
Fig.3 Test configuration
I
I
400
.~.
~
400
,
.~ ..
~
OUTPUT
380/400
CONTROL
INPUT
NOTE. T MAY BE LESS THAN OR GREATER THAN ,.
Fig.5 Timing diagram
102
'" t~~
"""00"
~r-n o,e"""o,
'"
'~
FigA Typical application with combined input
NUMBER OF
INPUT CYCLES
CT2012
PLL SYNTHESISER FOR TV
The CT2012 forms the heart of the Plessey Key Frequency Synthesis Tuning System by taking data from the
system control and data highway (the Keybus) when TUNE
or FINE TUNE code is recognised and then using this data
to control the frequency of the local oscillator in a television tuner with a phase locked loop (PLL).
oawNJLI COMPARATOR'
23
'KEYBUS'
DATA
UP
HIGHWAY
-u-
OUTPUT
INPUT
FEATURES
"PX
QUARTZ CRYSTAl
CLOCK
•
High Sensitivity Divider Input
•
Improved Control of Two-Modulus Divider
•
•
Fully Keybus Controlled
On-chip Frequency Standard and Comparator
•
FOljr Band Selection Outputs
2.5kHzClOCK
6
NOT CONNECTED
7
ABSOLUTE MAXIMUM RATINGS
+ 7V
Supply voltage, Voo
PinVoltage,pins9-13
+14V
Voltage, all other pins
+ 7V
Operating temperature range -10°C to +65°C
-55°C to+125°C
Storage temperature range
18
CRYSTAL TRIMMER
16
MODUlUS CONTROL
.DP24
Fig.1 Pin connections
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Tamb = +25°C, Vcr, = +5V
Test circuit: Fig.3
Characteristic
Operating voltage range
Supply current
Keybus inputs, high
low
Intemal pullup resistor
,;,'N input, peak-peak swing
Internal capacitance
External frequency standard input, pin 20 not
high
connected
low
Quartz crystal standard
AV Band and enable inputs
Band and AVoutputs,
unselected
selected
,;.N output,
Pin
Min.
4.5
8
8
1-5 Voo-1
1-5
2
1-4
200
21
Value
Units
Typ_ Max_
22
5.5
45
4
0.8
6
10
21
18 Voo-1
18
18,20
14,15 Voo-1
14,15
9-13
high
9-13
19
low
19
4
Conditions
V
mA Outputs unloaded
V Leakage 1Of'A max.(Pin50nly)
V
kn
mV Sine wave via extemal
capacitor
pF
100f'A max. sinking
100f'A max. sourcing
MHz 20 pF paralle'l resonance
V Leakage 10f'A max.
0.8
V
13.2
V Free drain, leakage
1Of'Amax.
1mAsinking
V
5
7
V Free drain, leakage
0.8
V
V
0.4
V
10~max_
0.3mAsinking
103
f-------1 f------'''"- ~g~~~g~
+N OUTPUT
TO
"RICAe
CONTROL
INPUTS
ON CT2017
{-c~=-----o<
JL..::n:::-------'____r-II---l
"'
DOWN
4MHz
QUARTZ
CRYSTAL
I---+---------~_"_ 2·5kHz CLOCK
L-iC=____________rc.. 50kHz
CLOCK
- " ' - - - - - _ . VSS
Fig.2 CT2012 block diagram
Apart from the CT2012 and the tuner, the PLL needs
two other integrated circuits: a .;-3BO/400 PRESCALER (the
CT2010) and the synthesisertuning interface (the CT2017),
which includes a charge pump, an active filter and an
output stage to drive the varicap line which controls the
local oscillator in the tuner.
In a typical system re·tuning of the television
receiver will come from a control circuit (such as the
CT2014) following some input from the viewer. This input
will be new channel, fine tuning information or an instruc·
tion to access a word of non-volatile memory. In every case,
the control circuit will send the required channel and fine
tuning information to the CT2012.
The FINE TUNE code is used to directly transfer the
FINE TUNE number from the control circuit to the syn·
thesiser and is separate from TUNE to reduce the highway use and the time delay during manual and auto·
matic adjustment tuning.
The CT2012 contains six main parts:
(a) A section to recognise the TUNE code (hexadecimal
10) or FINE TUNE code (hex. 1E) on the Keybus and
then to latch all of the relevant tuning information.
(b) A 10 bit programmable divider with an amplifier on its
clock input to allow use of a small swing on the output
of the PRESCALER and hence to reduce radiation.
(c) A fine tuning system which generates the correct
pulses to control the modulus of the prescaler and so
give a small shift in synthesised frequency.
(d) A crystal oscillator circuit (for 4MHz crystal) and fixed
.;-1600 divider to give 2.5kHz comparison frequency
and fine tuning timing.
(e) A phase and frequency comparator driven by the programmable divider and the fixed divider.
(f) Logic for band decoding and for video time-constant
switching for audio visual (AV) mode logic.
The Keybus highway is used to carry both instructions
and data around the Key System. To separate these two
functions the codes are transmitted when the Multiplex
Clock is low and the data when it is high; all zeroes or all
ones are inserted to fill the gaps between adjacent code or
data words to avoid spurious instructions. In order to improve the system's immunity to noise on the highway the
Multiplex Clock may be stopped between operations so
104
that noise is not clocked into any circuit, and so should
have no effect, and ideally the highway and Multiplex Clock
lines will be stopped in their lower impedance state to reo
duce noise amplitudes.
It is expected that all devices driving the highway will
have Open Drain outputs, for which pull-up resistors
(nominaI4krl) are included in the CT2012.
To safely detect control codes edge sensitive latches
are clocked on the rising ('0' to '1 ') edges of the Multiplex
Clock and have their inputs driven by gates looking for a
TUNE code (0001 followed by 1101) or a FINE TUNE (0001
followed by 1110).
Time
CI
C2
State
H3
H2
HI
HO
0
1
0
1
0
0
1
1
DI
D2
D3
D4
D5
D6
D7
DB
Remarks
Control code
Not used by Synthesiser
B1
07
03
0
P3
BO
06
02
0
P2
09
05
01
0
P,
OB
04 Band (B), Frequency (0)
00 and Fine Frequency (P)
P4 from Key.
PO
Table 1 Tuning sequence on Keybus
Time
CI
C2
D1
D2
State
H3
H2
HI
HO
0
1
0
1
0
1
1
0
Remarks
Control code
Oc2 Oc l OcO Pc4 Correction tuning
Pc3 Pc2 Pc1 PcO
Table 2 Correction tuning sequence on Keybus
Pin
High (source current)
Voo -O.SV min
Low (sink current)
O.4V max
2.5kHz Clock
6
0.5mA
2.0mA
UP
22
23
17
0.1mA
0.8mA
16
0.1 mA
0.3mA
Signal
DOWN
50kHz Clock
Modulus Control
.Table 3 Logic output currents
Pin No.
Name
8
24
Voo
Vss
;0
1
2
4
HO
H1
H2
H3
Four line highway, HO is LSB.
Inputs, OV and 5V logic levels nominal.
4K±50% pull·up resistors (to V oo ) in
device.
5
MULTIPLEX CLOCK
Highway timing input, OV and 5V nominal logic levels.
6
2.5 kHz CLOCK
2.5kHz output from crystal via reference divider. May
be used to give Multiplex Clock.
17
50kHz CLOCK
50kHz output from crystal via reference divider. Use
when selting crystal trimmer.
22
23
DOWN
16
MODULUS CONTROL
3
UP
Function
V } Power supply
lcomparator outputs to
Increase frequency when lo~ charge pump in Tuning
Decrease frequency when high Interface IC
KEYBUS
Outputs
with
OVt05V
nominal
swing.
Controls PRESCALER division ratio by pulsing high
up to 38 times each comparison cycle.
One crystal pin and the fixed capacitor.
20
QUARTZ CRYSTAL
18
QUARTZCRYSTAL TRIMMER
21
7N INPUT
12
9
11
10
13
BAND1
BAND3
BAND4
BAND2
AV OUTPUT
14
AV BAND
15
AV ENABLE
Selects shorter time constants for locking television
receiver to video tape recorder or equivalent. Will be
driven by diode decoder from Programme Number
lines. High for AV mode, only operative when AV
band is selected.
19
7N OUTPUT
Output of programmable divider provided for test
purposes only.
Second crystal pin and trimmer capacitor.
Low level input clock to Programmable Divider. Shou Id
be AC coupled.
Band output selected by code 00
Band output selected by code 01
Band output selected by code 10
Band output selected by code 11
Time constant switch, pulls low only if AV band
selected and AV enable is high
Open drain
outputs for
external
pull·up
to +12V.
Input from band switch to allow AV mode to be
selected.
105
TUNING RANGE
Combining the Fine Offset range, 0 to 19 steps of
50kHz with the Programmable Divider range, 80 to 1023
steps of 1MHz, allows tuning of the local oscillator for all
television broadcast channels in bands I, III, IV, V, to within
25kHz. In practice almost all television channels are
integer multiples of 50 kHz and so may be received
EXACTLY (apart from any slight crystal or IF error).
The correction tuning system gives a range of -3.95 to
+ 4.00 MHz in 50kHz steps around the nominal frequency.
CT2017
2'5kH: CLOCK o--~--a
.12V
BAND
,-
[ j - - - - - - - t - - AV ENABLE
SELECT
OUTPUTS 4
OOk
Flg.3 CT2012 test and application circuit
REFERENCE
ClOCK
-t~L
______ .--.JI (L -
I
I
PROGRAMMABLE
DIVIDER
UP
~
I
I
,
I
______
~
I
-U---------+i-:------,
I
DOWN _ _ _ _ _ _ _ _ _ _ _ _ _
11'-_____
Fig.4 Phase comparator timing
MULTIPLEX CLOCK
MuHlplex Clock:
Inslruclian or dala lime (I, or 10 )
Rising or falling edge lime (IER or I EF )
Dala or Inslructlon 10 clock sel·up lime (los or I,s)
Clock 10 dala or Inslructlon hold lime (IOH or I'H)
Operating frequency range of Multiplex Clock
+ N'N frequency
Flg.5 Dynamic characteristics
106
1"sminimum
200ns maximum
400ns minimum
100ns minimum
DC-500kHz
2.BMHz maximum
100kHz minimum
,
,
.
,r---.,
......J ____ ' - - - , _ . __
MULTIPLEX CLOCK TUNE
TUNE
DATA
DATA
DATA
OATA
DATA
KEYBUSCONTENT--·COOE--·COOE------- 01 - - - 02 - - - "03·--- 04"---" 05 - - -
Cl
C2
0001
1101
INFORMATION LATCHED
t
~
PRESCALER OUTPUT (';'N IN )
40XREFERENCE
t
t
t
JlJ1JUUl
JU"--uL ____ JUULrL ___ nJ1n
FRECUENCY
REFERENCE FREQUENCY
L __
------.r-------~
fiNE TUNING CORRECTlQN
_____ ~
fiNE" TUNING
Fig.6 Simplified timing diagrams
107
108
•
PLESSEY
Semiconductors
CT2017
SYNTHESISER TUNING INTERFACE
The CT2017 is designed for use in Frequency Synthesis
Tuning Systems, in particular the Plessey Key System.
The device contains a charge pump with a high
impedance voltage follower, a signal detect circuit, a
digital AFC circuit and a power on low detect circuit.
FEATURES
VCCII+12V1 [ ,.
•
•
17 ]
COINCIDENCE FIlTER [ 3
LINE Fl YBACI( INPUT [ 4
CT2017
Signal Quality Detector
•
•
AFC Input Option
Auto Up, Auto Down Logic Level Tuning
Correction
16 PAfe omCTOR INPUT
150 POWEAlOW
12P VCC12(+33V)
VARICAP CONTROL VOLTAGE OUTPUT [ 1
Logic Level Control
CONTROL OUTPUTS
13P DV
VCCS(+5VI [6
Active Filter Charge Pump
I
AUTO DOViN CORRECTION TUNING
14 ~ POWER LOW DETECTOR DElAY CAPACITOR
5
Low Varicap Driver
•
•
,,]'UTOUP
SIGNAL DETECTOR ENABLE INPUT [ 2
-VE VIDEO INPUT [
•
'-J
CHARGE PUMP FILTER [ 8
n
CURRENT REFERENCE [ 9
10
pUP
v
PDOWN!1-
I
VARiCAP CoNTAOl
INPUTS FROM CT2!l12
OR SIMILAR CIRCUIT
DP18
Fig.1 Pin connections
Power Low Detector
RESET OUTPUT
1-----<;" ....-/'--~~;~ 0'--..---------1
L-_ _ _ _ _---l-+-H++-+-~::
:gIT--t--H-i-+t+-l::
CONTROL
D.
7~~Jt~~+-t-,
--QH+-1-+H--H"
3~----C~~
-2tts-t-+~:+o~H-+--l1S
2~-----C=r--+
lOOk
"
NEONS·
VITAUTY
02
TYPE 3L
IO.
VDD __
~~k~~-+
___________
Fig. 3 Typical application circuit
Reset output
118
=
CHl . CH2' CH4' CH5· CH6
=
1 +2+3+4+5+6+3
~
__
Units
Condition
J1.A
rnA
Yin = OV
n
n
lout = 10mA
lout = 4mA
V
V
lout = 0.5mA
CONSUMER
lVCIRCUrTS
ML232B
MOS TOUCH TUNER
The ML2328 is a six-channel sense circuit designed
specifically for touch tuning in colour and monochrome
television receivers_ Using low threshold P-MOS technology,
the circuit can be driven directly from two-terminal touch
plates - replacing conventional mechanical push-buttons
for channel selection_ Neons may be used to indicate the
selected channel, while the latched output of the ML2328
drives the varicap tuner via a bias selection network_
A stepping facility is included whereby the application
of a suitable negative-going pulse to the step input pin, will
cause the selected channel output to advance by one_
~
Vsy[ 1
r
[
VARICAP
OUTPUTS
ABSOLUTE MAXIMUM RATINGS
-1 oOe to +65°e
-10o e to +85°e
Supply, Vss-Voo
Varicap voltage Vsv w.r.t. Vss
36V
+O.3V
.
[s
•[
7
""ss [
8
P""oo
,"P]
'" "pP
P
liP
lOP
C",
13
SENSE INPUTS
12
INDICATOR OUTPUTS
CH'
H'
CHi
9
P
STEP INPUT
OP16 OG16
Fig.' Pin connection$
FEATURES
•
•
•
l
[,
[
Ambient operating temperature
Storage temperature
16
c",
Six-channel Capability
Direct Neon orLED Drive
Low Impedance Drive to Varicap
•
•
•
Uses 33V Varicap Supply
Low Current Drain
Remote Control Stepping Facility
SENSE INPUT
INDICATOR OUTPUT
i- ~- --T-t~--T-f--1-f--'-f-- -r-fO--1-----l
I
I
I
I
I
I,
II:
I
I
:
I
VS5
'2 1
I LATCH
YS)I
:I
I
I
I
I
I
!
CLOCk
GEN
I STEP
INPUT
~9
~
U
I 'JDc
~
l ,---L~--L+--L+--Lt.--i+--L---J
VAR1CAP
OUTPUT
Fig. 2
Functional diagram
119
ML232B
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Tamb = +25°C. Voo = O. Vss = Vsv = 30V to 36V
Value
Characteristic
Typ.
Min.
Input current
Supply current
RON of varicap switch
RON of indicator switch
Sense input threshold
Step pulse level
Step pulse width
O.4V ss
0
0.1
I~~~
2l.OY AC
Yin = OV
n
n
. lout = lOrnA
lout = 4mA
V
V
rns
lS
lOOk
:r..
TOUCH
PlATES
6-8'"
9
~
~
~
NEONS
ID
II
Il
"
"
TYPE 3L
""
.
)J
Fig. 3
Vss. Vsv
TO VARICAP
CONTROL
., 1
'"
•
,
,
"
]
IS
2
"
NEONS
VITALITY
120
/J.A
rnA
~o.
03
'00
Condition
1
5.5
100
250
0.6Vss
Vss-29
1
4
50
125
0.5V ss
2
Units
Max.
,
".
Typical application circuit
"'"
02
iTamb
= DoC to +65°C
CONSUMER
lVCIRCUITS
ML2368
6-CHANNEl CASCADABlE TOUCH CONTROL INTERFACE
The ML236B is a six-channel sense circuit designed
specifically for touch tuning in colour and monochrome
television receivers_ Using low threshold P-MOS technology,
the circuit can be driven directly from two-terminal touch
plates - replacing conventional mechanical push-buttons
for channel selection_ Neons or LEOs may be used to
indicate the selected channel, while the latched output of
the ML236B drives the varicap tuner via a bias selection
network_
A stepping facility is included whereby the application
of a suitable negative-going pulse ca'uses the selected
channel to advance by one_
CLEAR INPUT
r"
V"
VARICAP
St:RIALIN
"
"
INPUTCH 2
,
OUTPUTS
"
OUTPUT CH 4
"
"
"
OUTPUT CH 5
OUTPUT CH 6
MUTE SWITCH 1
Vss
MUTE SWITCH 2
•
"
v"
'-"I
INPUT CH 3
INPUT CH 4
SENSE
INPUTS
INDICATOR
OUTPUTS
INPUT!:H 5
INPUT CH 6
NO CONNECTION
P
"P
"
1
MUTE SENSE INPUT
"
SERIAL OUTPUT
STEP INPUT
"
DP24
6-Channel Capability - Cascadable
Direct Neon or LED Drive
Low Impedance Drive to Varicap
Uses 33V Varicap Supply
Remote Control Facility
A Negative Pulse on Clear Resets
All Channels
I"!PUT
,----
Fig. t Pin connections
ABSOLUTE MAXIMUM RATINGS
_10°C to +6SoC
_10°C to +BSoC
Ambient operating temperature
Storage temperature
Vss -Voo supply
Varicap voltage Vsv
36V
Vss +O.3V
CHANNEL SENSE INPUTS
INOICAJOR OUTPUTS
r.lUTE
SE,",SE
i~l
--r-"
~6
CH3
----------~-t-,-t-rt-rt-r--t---i----I
I
I
Vss
2l
OUTPUT CH 3
FEATURES
I
...r--;7
OUTPUT CH 2
RESET OUTPUT
•••
••
•
,
2
I
1 JvW;l
t~
l0t----H-t-'H====::;-r-
I
I
I
I
RE:OET
OUTPUT
.. utE
SWITCH 2
SERIAL
OUTPUT
Sl~~::rt
\ls v
2
<>--------'-----.--:--+-+---+---+---+----4-I
I
I
I
IL _______ l.
I __ _
CLEAR
IIIIPUT
, ________ L+_L~-L~-L+-L-+--
-42, Voo
_"': __ ...1
'"'
VARICAP OUTPUTS
Fig. 2 ML236'B functional block diagram
121
ML236B
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated!:
Tamb = +25°C, Voo = 0, Vss = Vsv = 30V to 36V
Value
Characteristic
Min,
3
Supply current
Input current
RON of varicap switch
RON of indicator switch
Vth sense lIP threshold
Clear, step pulse level
Ts step pulse width
Clear pulse width
RON of mute switch
Serial and reset alP
Vss-1
Serial and reset lIP
Vss-1.5
NOTES
Stepping selection:
Units
5
1
125
250
0.6
Vss-10
1
60
125
0.5
0.4
0
0.2
0.2
100
~A
VIN = 0
lOUT = 8mA
lOUT = 4mA
Q
Q
Vss
V
ms
ms
lOUT = 5mA
'1 '
'0'
'1 '
'0'
Q
200
Vss-11
Vss-10
V
V
V
V
r--
INPUT
e
}
:
)
u
(CONNECTION WHEN
NOT CASCADING I
[CONNECTIONS 10'
~
~
03
10"
"
10 VARI CAP
"
---{ "
"
"
"
"
to
TYPE II
-
'00
•
•,
"
CONTROl
2
~
r---o
01
MUTE
SWITCH
f--<>
S
,
tOOk
~
MUTE SENSE
"~T
10
~
2l
r
""
,
,
2D
~
NEONS:
YlTAlITy'
"
,--
W
~o
~NS
~~JE~C~~~C~~~~SGI
1I1~~E:t
~~~~s~:::::
6·eN
02
Vss.Vsv
Fig. 3 Typical applications using neons as channel indicators
122
mA
Vss--,
voo----L......J
..... 15 _
STEP
lOOk
Conditions
Max.
Typ.
ML236B
APPLICATION NOTES
Application using LEOs as channel indicators
In applications where the use of mains is not desired
channel selection can be made by using the +30V Vss
supply as a compromise but at the expense of reduced
input sensitivity. In this case LEDs can be used as
channel indicators.
Sensitivity may be improved at lower voltage by using a
tapped LED current limiting resistor to derive a higher
input voltage. (Fig. 5)
"''''''''''''"T+
!
~
:~~;,
.~
,
IJJJJ
,.
Iff
,'fJ~,t..
II
II
,., ; t t
r-
L,~
::
"",...,~
--
"
"
~"
~
~'"
'M
Fig.4
t2-channs/ application using LEOs as indicators
TOUCH
PLATES
INPUT
ION
Fig. 5 Improved sensitivity for 33V operation
123
124
CONSUMER
TV CIRCUITS
ML237B
6-CHANNEL TOUCH CONTROL INTERFACE
The ML237B is a six-channel sense circuit designed
specifically for touch tuning in colour and monochrome
television receivers. Using low threshold P-MOS technology,
the circuit can be driven directly from two-terminal touch
plates - replacing conventional mechanical push·buttons
for
channel selection. Neons can be used to
indicate the selected channel, while the latched output of
the ML237Bdrives the varicap tuner via a bias selection
network.
A stepping facility is included whereby the application
of a suitable negative-going pulse to the step input causes
the selected channel output to advance by one.
INPUTCH 1
SE,lj3E
INPUTS
NEON
OUTPUTS
INPUT CH Z
,
INPUT CH 3
J
INPUT CH 4
,
INPUT CH 5
5
INPUT CH 6
,
MUTE TIMING
B
CONTROL
••
••
••
••
"
"
"
1)~
6
STEP INPUT
FEATURES
"
OUTPUT CH 1
OUTPUT CH 2
OUTPUT CH
J
VARICAP
OUTPUTS
OUTPUT CH 4
OUTPUT CH 5
12~ OUTPUT CH 6
V"
6-Channel Capability
Di rect Neon Drive
Low I mpedance Drive to Varicap
Uses 33V Varicap Supply
Remote Control Stepping Facility
Sound Muting During Selection
Selected Channell on Power-up
Channels Are Selected With a Negative (or
Earth) Input
Voo
11~
MUTE OUTPUT
10~
Vsv
DP18
Fig. 1 Pin connections.
ABSOLUTE MAXIMUM RATINGS
Ambient operating temperature
Storage temperature
Supply, Vss-Voo
Varidlp voltage Vsv
SENSE INPUTS. NEON OUTPUTS
-10°C to +65°C
_10°C to +85°C
36V
Vss+O.3V
MUlE
TIMING
r-+---Voo
CONTROL
c_
--rf---r+----~+- -Tt'----,-t'---T-----,
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
18 1
I
I
STE'P
INPUT
I
I
I
'55
'00
10:
IISV
L.r
I
L+ __ L
:
ii--
I
I
I
I
I
I
I
-Li;s- -
I
r.. -,
~~
--t,,---:-t;;----tii---1-io-- 1--- - J
CHI
CH6
,
/oIUTE
~~
VARICAP OUTPUTS
Fig. 2 Functional block diagram
125
ML237B
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated):
Tamb
= +25'C, Voo = 0, Vss = Vsv = 30V to 36V
Value
Units
Characteristic
Min.
I nput current
Output leakage
Mute switch O/Pleakage
Supply current
Ro N of varicap switch
Step pulse width
Neon switch output current
Mute switch Ro N
Input threshold
Step input current
Mute period
Step pulse level
1
1
10
/.IA
/.I A
rnA
n
100
0.2
2
200
0.6
1000
100
0.5
400
0
VIN = Vss
VOUT = 0
V OUT = 0
/.I A
8
5
50
0.4
10
Conditions
Max.
Typ.
Vss-29
lOUT = 10mA
>.05Tm
ms
mA
n
lOUT = 5mA
Vss
VIN =0
CM = 0.68 /.IF
/.IA
rns
V
NOTES
The mute timing can be increased by using a higher value of capacitor (eM)
Touch plate selection:
MUTE
WlPU!
____
--1_ I.
V55
VDD _ _ _ _
I--
-'~
Tm :::: Cm x 0.6ms/nF
If the channels are selecting by stepping then the mute output is extended by the clock pulse width TS
SrEf>
Stepping selection:
INPUT
"""
OUTPUT
~~
'V
'WV
02
L7k
'~~
ntJ
TOUCH
I,:ATES
,"
~
YRI: BVeBO' BVCEO > ISOY
,10k
'/a)
.,
II
,
.
,
=S
~s
tj
YARICAP
5
•
,- 7
TO"
Voo
Vss, Vsv
Ii:
1~~~1J
.
17
1
CONTROL
0'
"
"
"
'00'
11
TO
Jl
MUTE OUTPUT.
Fig. 3 Typical applications using neons as channel indicators
126
CONSUMER
TV CIRCUITS
ML2388
8-CHANNEL TOUCH CONTROL INTERFACE
The ML23BB is an eight channel sense circuit designed
specifically for touch tuning in colour and monochrome
television receivers. Using low threshold P·MOS technology,
the circuit can be driven directly from two-terminal touch
plates - replacing conventional mechanical push·buttons
for channel selection. Neons or LEOs may be used to
indicate the selected channel, while the latched output of
the ML23BB drives the varicap tuner via a bias selection
network.
A stepping facility is included whereby the application
of a suitable negative-going pulse to the step input causes
the selected channel to advance by one.
"0 CONNECTION
(
1
INPur CH I
,
"23P
INPUT
CH 2
3
22~
INPUT
CH l
,
SENSE
INPuTS
INPur
CH
~
5
INDICATOR
OUTPUTS
INPUT
•
'" 5
INPuT
.
CH 6
OUTPUT CH
~
CH 5
CK 8
3
,P
\P
OuTPUT CI-I a
STEP INPUT
'0
'" 7
CH 7
MUTE OUTPUT
I
CLEAR INPuT
"
'55
OUTPUT
,P
HP
IlP Vsv
"
CONTROL
VARICAP
OuTPUTS
OUTPUT
OUTPUT CH 6
MUTE TIMING
••
••
••
••
•
OUTPuT Crl 3
lap
INPUT
8-Channel Capability
Direct Neon Drive
Direct Neon or LED Drive
Low I mpedance Drive to Varicap
Uses 33V Varicap Supply
Remote Control Stepping Facility
Sound Muting During Selection
Selects Channell on Power-up
A Negative Pulse on Clear Resets to Channell
OUTPUT CH I
OuTPUT CH 2
7
INPuT
FEATURES
21b
20b
19b
'DO
DP24
Fig 1 Pin connections
ABSOLUTE MAXIMUM RATINGS
Ambient operating temperature
Storage temperature
Supply, VSS-VOD
Varicap voltage Vsv
_10°C to +6SoC
-10°C to +BSoC
36V
Vss +O.3V
SENSE INPUTS. INDICATOR OUTPUTS
CH 8
~U~6N~~~~G
-
rt---"T- ~---Tt!---rt~---rt~---dz.---;-t~---d~- -d~---T
I
:
I
I
I
I
I
1
I
I
I
J
I
I
I
I
I
I
I
I
I
I
I :
I
r
I
I
I
"S5 12 I
I
I
I
I
I
I
I
I
I
I
I
I
I
t
I
I
I
I
I
I
I
I
I
I
III 1I
I
I
I
I
I
I
I
I
1
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
'V
22
T21
l20
l19
,
l'8
J
CLEAR INPUT
I
--, r
I
-. r
'.'ss
U
'.'00
I
L...J
OIC
Voo
STEP INPuT
I
C H I '
I
~
I
VSV 13'
l_Ll __ L ____ l...L __ LL __ .LL __ l...L __ ll
----,
1
1~
J
!u
--r-Voo
-l17-- -li6-- -fs-- ----CKB
V
I
J
MUTE
~~
'.'ARICAP OUTPUts
Fig. 2
Functional block diagram
127
ML238B
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Tamb = +25°C, Voo = 0, Vss = Vsv = 30V to 36V
Value
Characteristic
Typ
Min
Output leakage
Supply current
Input current
RON of varicap switch
RON of indicator switch
liP threshold
Step pulse level
Ts step pulse width
Clear pulse level
Clear pulse width
RON of mute switch
Tm mute timing
Step liP current
Mute OIP leakage
1
g
1
100
300
0.6
Vss-29
6
50
180
0.5
0.4
0
0.2
0
0.2
Units
Max
VOU! = 0
~A
mA
V;o = OV
lOUT ~ 10mA
lOUT = 10mA
~A
n
(1
Vss
V
ms
V
ms
Vss-29
100
400
>.05 Tm
n
200
lOUT ~. 5mA
em = 0.68~F
V;o = 0
VOUT = 0
ms
~A
~A
1000
10
10
NOTES:
The mute timing can be increased by using a higher value of capacitor (em) (See Fig. 4).
iT"r
Touch plate selection:
,",UTE
OUTPUT
'ss - - - - - , - ,
L--
--'1
'00 _ _ _ _
. Tm"'C m x
O.6ms/nF
If the channels are selecting by stepping then the mute output is extended by the clock pulse width Ts.
STEP
INPUT
Stepping selection:
,",UTE
OUTPUT
The clear lIP should be left open circuit when not in use.
,
2 0'0' AC
0""
lOOk
....QQ..~
~ ~ ~ ,J >I ,J ,J ,J ~e~f~s
VARICA P
CONTR OL
6-8'"
0'
-,
I:$
-Qs
m"
2
3
,
22
"
20
6
"
"
"
"
"
7
,
9
r---
"
"
5
m
t"r"
lOOk
"t--.
02
"~
vSS,vsv
'DO
STEP PULSE
CLEAR lIP
1J
1J
",UTE OIP
n
Fig. 3 Typical applications using neons as channel indications.
128
Conditions
ML238B
APPLICATION NOTES
Application using LEOs as channel indicators
In applications where the use of mains is not desired
channel selection can be made by using the +30V Vss
supply as a compromise but at the expense of reduced
input sensitivity. In this case LEDs can be used as
channel indicators.
The 1.2k 0 and 8200 resistors limit the LED current to
10mA, whilst the diode ensures less than 1 ~A leakage
when the LED is reverse biased. It is desirable to have a
1 MO resistor between the touch plates and the input
as a safeguard against static.
On selection of a channel, the potential divider chain
comprising the 1 MO resistor, the finger resistance and
the 10MO resistor sets the threshold voltage on the
input pin. When the channel isselected the Ie provides a
current source to the LED.
j'.'SS
"
'"
"
".
-,
LEDS
"
"
"
"
~
0'
"
2
13
3
22
,
S
,
7
,
"
20
"
"
,
"
"
r-- "
"
Iff'r"
"f--
"
".
ICAP
CON TROL
~
1'2~
~-
~ ~ ~ ~ ~ ~ ~ ~ ie~i~s
e.
100~
02
"~
"55, "S'I
820
'DO
STEP INPUT
CLEAR liP
,",UTE O/P
Fig. 4 Low voltage, improved sensitivity using LED indicators
129
130
PLESSEY
Semiconductors
•
CONSUMER
TV CIRCUITS
ML2398
8 - CHANNEL TOUCH CONTROL INTERFACE
The ML239B is an eight channel sense circuit
designed specifically for touch tuning in colour and
monochrome television receivers. Using low threshold
P-MOS technology, the circuit can be driven directly
from two-terminal touch plates - replacing conventional mechanical push-buttons for channel selection.
Neons can be used to indicate the selected channel,
while the latched output of the ML239B drives the
varicap tuner via a bias selection network.
A stepping facility is included whereby the application of a suitable negative-going pulse to the step
input causes the selected channel output to advance
by one.
,
NO CONNECTION
INPUT Ctl 1
INPUT
OUTPUT CH I
]
22
OUTPUT CH 2
CH 2
,
,
SENSE
INPUTS
INPUT CH':
NEON
OUTPUTS
INPUT
Ctl 5
[
INPUT
CH 6
[
INPUT
CH 7
[
INPUT
CH 8
FEATURES
,
..
8-Channel Capability
Direct Neon Drive
Low Impedance Drive to Varicap
Uses 33V Varicap Supply
Remote Control Stepping Facility
Sound Muting During Selection
Selects Channel 1 on Power-up
A Negative Pulse on Clear Resets to
Channel 1
Channels are Selected with a Negative
(or Earth) Input
21
OUTPUT CH 3
20
OUTPUT Ctl ,
"
"
,p
CMJTPUT CH 5
.,
,
,p
,p
"p
10
MUTE TIMING
CONTROL
11
17P
["
'ss
'OD
2l
STEP INPUT
..
..
..
..
..
..
..
..
24
[ 2
VARICAP
OUTPUTS
OUTPUT CH 6
OUTPUT CH 7
OUTPUT
CH 8
CLEAR INPUT
'sv
DP24
Fig. 1 Pin connections
ABSOLUTE MAXIMUM RATINGS
Ambient operating temperature -1 DoC to +65°C
Storage temperature
-10°C to +85°C
VSS-VDD supply
36V
Varicap voltage Vsv
Vss+O.3V
SENSE INPUTS, NEON CUTPUTS
I
\
CH 1
CH 8
MUTE TIMING
r~-- T '--Tf---r¥--,+--r t~--,-t~---i!._-~~~R:-T ---l
I
I
I
I
I
I
I
:
I
I
:
:
I
I
I
I
I
I
I
I
I
I
~II
I
I
I
t
I
I
:
,,,_'''1]Ir-----nr---!;------+------+---
:
I
I
'00
I
:
I
"I
I
I
I
U
I
I
_--1-?21--1-1
I
I
iO - -
I
-fI
CLEAR INPUT
---,
r O /C
L-.J
Vee
I
110
.STEP INPUT
-,
I
I
'
Lti9- _l_!18-_L~- _L!i6 - -tiS -.J
____________________~V~__________________~:J~8
;~H'
II
.J. -
U
rVSS
Voo
-¢1L- "'ss
I
-
_.J
MUTE
OUTPUT
VARICAP OUTPUTS
Fig. 2 Functional Block Diagram
131
ML239B
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated):
Tamb = +25°C, Voo = 0, Vss = Vsv = 30V to 36V
Value
Characteristic
Step, clear pulse level
Input current
Output leakage
Mute switch OIP leakage
Supply current
RON of varicap switch
Clear step pulse width
Neon switch output
current
RON of mute switch
Input threshold
Step input current
Mute period
Units
Typ
Min
Conditions
Max
Vss-29
1
1
10
9
1000
0
6
50
0.2
V
VIN = Vss
VOUT = 0
VOUT = 0
~A
~A
~A
mA
n
lOUT = 10mA
>.05Tm
ms
2
200
0.6
1
100
0.5
0.4
10
mA
400
n
lOUT = 5mA
Vss
mA
ms
VIN = 0
CM = 0.68~F
NOTES:
The mute timing can be increased by using a higher value of capacitor (em)
NIl"
Touch plate selection:
OUTPur
i'"r
Vss - - - - - , - ,
L--
voo----I
Tm",C m X O.6ms/nF
If the channels are selecting by stepping then the mute output is extended by the clock pulse width Ts.
STEP
INPUT
Stepping selection:
IOU"
OUTPUT
The clear I /P should be left open circuit when not in use.
Voo
+""150'"
'"
,,,
~'I-
VARICAf'
m
TR1: evCBO. evCEO "" 150'0'
1070k
'"
CONTROL
-,
I
TR/I)
~"'~
02
I ~ ~ ~ ~ ~ ~ ~ ;e~i~s
~
IO"
Voo
24
2
21
,
,
'"
S
20
,
,
•
•
-10
Iff"r"
VS5. 'isv
"
"
"
"
"
IS
"r-
"1
STEP PULSE
CLEAR IfP
'"'UTE DIP
1.[
1J
Il
Fig. 3 Typical applications using neons as channel indications
132
ML920
REMOTE CONTROL RECEIVER
Plessey Semiconductors have developed and produced a range of monolithic integrated circuits which
give a wide variety of remote control facilities. As well
as ultrasonic or infra red transmission, cable. radio or
telephone links may also be utilised. Pulse position
modulation (PPM) is used with or without carrier and
automatic error detection is also incorporated. Although
initially designed with TV remote control in mind the
devices may equally easily be applied for use in radios,
tuners. tape and record decks, lamps and lighting, toys
and models, industrial control and monitoring.
The ML920 demodulates the PPM signal received
from the SL490 transmitter. After error checking the
received code may condition a 20 programme memory
or one of three Dj A converters.
•
II
•
•
•
I
2
VD,IOVI
,
ON/STANDBY INPUT
5
NQRMAUSEINPLJT
STEP INPUT
OSC. TIME CONSTANT
osc. MONITOR
PPMINPUI
O/ARHERENCE
"
BRIGKTNESS a,A
22
MUTE
"
1
!6VI
V,,(
21
VOLUMED/A
20
E
, ML92019
0
BINARY
PROGRAMME
•,
"
"
"
C
B
SELECTION
7
10
15
Oil
II
RECALL
12
"
IJ
A
STEP TIME CONSTANT
POWER CLEAR TIME CONSTANT
AFC
DP24
Fig, 1 Pin connections
QUICK REFERENCE DATA
•
II
COLOUR QtA
COLOUR KILL
Power supply: 16V 14mA
Demodulation: Pulse position with time
window checking by on-chip oscillator
Decoder: 5 bit with successive codeword
comparison
Programme: Latched 5 bit binary.
20 programmes
Analogue controls: 3 static current mirror
converters, 32 step with normalise level
Other outputs: On, Recall Display, AFC,
Mute, Colour Kill. Oscillator Monitor
Local inputs: On/Standby. Step,
Normalise
FEATURES
•
•
•
•
•
•
•
•
Accepts 5 Bit PPM
All Timing From On-Chip Oscillator
Incorporates Error Prot€ction
Easily Used With Ultrasonic or Infrared System
Up to 20 Programmes With Latched Binary
Output
3 D/A Outputs With Normalise Level At
~ of Max.
Automatic Power-On Reset and Normalise
Many Other Facilities, AFC, Mute, Colour
Kill. Recall etc.
PPI1,NPUT
PO .... fR (LEAR 14
TIME CONST
NORMALISE
STEP
PROGRAMME
STEPTIHE
(ONST
15
~~-,-_.,...,_--,
DIA
REFERENCE
Fig. 2 ML920 remote control receiver block diagram
133
ML920
ELECTRICAL CHARACTERISTICS (see Fig. 3)
Test conditions (unless otherwise stated):
Vss= OV
VDD= -16V
Tamb = 25°C
Value
Characteristics
Pin
Typ.
14
Supply voltage
3
3
Supply current
-1
5,6,7,
Input logic level high
low
VDD
-1
Output logic level high 2, 11 -1 3, 16-20, 22
VDD
low
Analogue output
1,21,23
0
current range
(pins 1, 21, 23)
1,21,23
0
Analogue step size
24
-250
DI A reference, I REF
Oscillator timing
9
14
Power clear time
constant
15
Step time constant
-1
Monitor output 'high'
9
'Iow'
Voo
PPM input logic level high
-1
PPM input logic level low
10
Voo
PPM input pulse width
1
INPUT
;
.
,
I"
1
8
-345
1.5k
400
50k to VOD
50k to VDD
31
8
IREF
3.9k to VDD
1
IREF
Vou, < VDD +5V
33k to Voo
C = 22ri, R=100kSeenote1
C = 4.7(.1 R=100k
"
-455
~A
Hz
ms
22Tosc
C = 470n R = 3.3M
Internal load
provided
s
V
V
V
V
0
Voo +0.5
0
-6
T~_1_
liS
fosc
1""
"
16~
"·r
lOOk
,,<
BC~
..r
~~I
I
VOL 21
10~
S'H
~~~~
Hl920
..
NO~I'I"'LIS£
ON!1
WI'
..
15 STEP lie
'-
" 11'
RECAll']
Af(
,
n
\loo~
,
" " " " "
-
'"
'"
~::::
-
'"
BI"I
" 11'
.n
0
."
l·ek
I'
t
1.
Kill?
1 SHP
PLESSEY
TBA 120u
l-
BRill
NORMAliSE]
I
7'~
110N~
f--" POWER TIC
V
mA
V
V
V
V
2
t1un21
~1"I
18
14
0
VDD +3.5
0
VDD+0.5
1
ose Ie
'S<
""'
ST.l.NOBY
ONISIANOBY{
SHP
PROG~AI1ME
Max.
8
t
=~i,"
~p",
Conditions
Units
Min.
.,.ifi
",
+I/V
PlESSEY
IDA 2560
1
AU RESISTORS 56, UNLESS OTHERIOISE $T.lHD
Fig. 3 PPM receiver application
PIN FUNCTIONS
Negative Logic: 0 is OV (Vss), 1 is -17V (Voo)
1,21,23. Colour, Volume, Brightness
These three outputs are from three 5 bit current
mirror D/A converters. They are referenced to the
current drawn from pin 24, I"" and give 32 steps,
"etl8 per step, from 0 to 31/8 I,e'. The outputs will be
set to 12/81", by the NORMALISE input, the normalise
code from the transmitter, or when the ON output goes
to a 1.
134
2. Colour kill
This output gives a logic 0 when the COLOUR D/A
output is zero.
3. Voo
-17V power supply
4. Vss
OV power supply
5. On/Standby input
A 1 on this pin will toggle pin 11 (ON O/P), generate
ML920
RECALL and AFC, normalise VOLUME, BRIGHTNESS
and CO LO U R, reset M UTE and set channel code
00000.
6. Normalise input
A 1 will normalise the VOLUME, BRIGHTNESS and
COLOUR outputs. A RECALL signal is generated and
MUTE is reset.
7. Channel step
The channel code will step up by 1 as long as this
pin is held at logic 1. The time period between steps
is defined by an RC constant attached to pin 15.
On reaching 20 the next step returns to 1. On output is
set to ON, and AFC is generated. If the TV goes from
Standby to ON, RECALL is generated and VOLUME,
BRIGHTNESS and COLOUR are normalised. If
VOLUME is not 0, MUTE is reset.
Oscillator time constant
An RC time constant is formed for the clock timing
by connecting external components, one resistor and
one capacitor, to this pin. Adjusted so that period of
output on pin 9 is 1/20 of 0 interval of incoming PPM.
9. Oscillator monitor
This output is a division of two of the oscillator, and
and is available for testing and setting purpose.
10. PPM I/P
The output of the front end amplifier is connected
here such that the signal i.s in the form of positive pulses
separated by time periods whose length define the
data. With no signal, PPM input is at a logic 1.
11. On O/P
Open drain output. Logic 1 denotes TV set ON:
Logic 0 TV set standby. Set to 1 when channel number
changes. Set to 0 by power clear or by transmitter
selected Standby. Toggle to opposite state by manual
ON/STANDBY control.
12. Recall O/P
Open drain output. A 1 may be used to trigger an
a,
Transmitter code
Function
EDCBA
000.00
00001
00010
00011
00100
00 10 1
a a 110
a a 111
01000
0100 1
01010
01011
01100
a 110 1
01110
01111
10000
10001
10010
10011
10100
10101
1 01 1 0
1 01 1 1
11000
11001
1 1 a1 a
11011
11100
11101
1 1 11 0
11111
Programme 1
Programme 2
Programme 3
Programme 4
Programme 5
Programme 6
Programme 7
Programme 8
Programme 9
Programme 10
Programme 11
Programme 12
Programme 13
Programme 14
Programme 15
Programme 16
Programme 17
Programme 18
Programme 19
Programme 20
Colour +
Programme Step +
Volume +
Brightness +
Standby
Mute
Recall
on·screen display. A static output is generated by the
manual controls ON/STANDBY and NORMALISE.
A pulse is generated by any channel change if the
circuit switches to ON at the time, and by RECALL and
NORMALISE commands from the transmitter.
13. AFC O/P
Open drain output. Logic 1 can inhibit the tuner AFC.
A static output is generated bymanual ON/STAN D BY
control. A pulse is generated by any channel number
change.
14, Power clear
A capacitor and resistor connected here define the
time delay for the power clear circuit, which normalises
all D-A outputs etc.
15. Channel step time constant
An R-C time constant defines the time period
between increments of the channel number when
stepping.
16 -20. Channel outputs
5 Outputs encode 20 channel numbers in binary
code
EDCBA
Channel 1 is 00000
Channel 20 is 1 0011
E is first and A is last in the PPM pulse train.
Channell is set when ON goes to a 1
21. Volume.
See Pin 1
22. Mute O/P
This will change state (toggle) on reception of a
mute command and VOLUME OIP is zero MUTE OIP
is held at O.
23. Brightness
See Pin 1
24. D/A Reference
A current drain lref, set by a single external resistor
will set the nominal step of the D/A outputs to Iretl8.
ABSOLUTE MAXIMUM RATINGS
(Vss= OV),
Supply Voltage VDD
Voltage at any input
Operating voltage range, VDD
Maximum power dissipation
Operating temperature range
Storage temperature range
+0.3V to -25V
+0.3V to -25V
-14Vto -18V
600mW
-10'C to +65'C
-55'C to +125'C
Normalise
Colour Programme Step Volume Brightness -
Table 1 Basic 32 command set
135
136
ML922
REMOTE CONTROL RECEIVER
Plessey Semiconductors have developed and produced a range of monolithic integrated circuits which
give a wide variety of remote control facilities. As well
as ultrasonic or infra red transmission. cable. radio or
telephone links may also be utilised. Pulse position
modulation (PPM) is used with or without carrier and
automatic error detection is also incorporated. Although
initially designed with TV remote control in mind the
devices may equally easily be applied for use in radios.
tuners. tape and record decks. lamps and lighting. toys
and models. industrial control and monitoring.
The ML922 demodulates the PPM signal received
from the SL490 transmitter. After error checking the
received code may condition a 10 programme memory
or one ofthree D/A converters.
The receiver timing may be set by adjusting the
oscillator time constant to give 40 periods at pin 6 equal
to a 0 interval on the received PPM input.
--..
D/A REFERENCE
L1
18
BRIGHTNESS D/A
COLOUR D/A
2
17
MUTE
VOIO (OY)
1
16
V"I+16V)
4
ML922
IS
STEP INPUT
5
14
osc. TIME CONSTANT
6
"
PPMIHPUT
7
ON
•
"
1\
VOLUME D/A
.
0
C
A
STEP T1MECDNSIANi
Aie ......_ _ _"... POWER ClEAf! TIME CONSTANT
DP18
Fig. 1 Pin connections
FEATURES
QUICK REFERENCE DATA
•
•
•
•
•
•
Accepts 5 Bit PPM
All Timing From On-Chip Oscillator
Incorporates Error Protection
Easily Used With Ultrasonic or Infrared System
Up to 10 Programmes With Latched
Binary Output
3 D/A Outputs With Normalise Level At
i of Max.
Automatic Power-On Reset and Normalise
Many Other Facilities. AFC. Mute. Etc.
•
•
•
•
fOIo'(ActUR
''''[
10
(O~SI
."
lOC;I[
SliP
~
PRO~R""'''[
\'g"~i"[ "'''~--l.-"T"T_...J
,.
R[HAIIIC[
Fig. 2 ML922 remote control receiver block diagram
•
•
•
•
Power supply: 16V 14mA
Demodulation: Pulse position with time
window checking by on-chip oscillator
Decoder: 5 bit with successive codeword
comparison
Programme: Latched 4 bit binary.
10 programmes
Other outputs: On. AFC. Mute
Local inputs: Programme step
Transmitter code
EDCBA
OOOOX
0001X
0010X
0011X
0100X
0101X
0110X
0111 X
1000X
1001X
10100
1 01 01
1 011 0
1 0111
11000
11 001
1101 1
11100
111 01
111 1 0
11111
Function
Programme 1
Programme 2
Programme 3
Programme 4
Programme 5
Programme 6
Programme 7
Programme 8
Programme 9
Programme 10
Analogue 1 +
Programme Step +
Analogue 2 +
Analogue 3 +
Standby
Mute (Analogue 2)
Normalise
Analogue 1Programme Step Analogue 2 Analogue 3 -
Table 1 Basic 21 command set for ML922
137
ML922
ELECTRICAL CHARACTERISTICS (see Fig. 3)
Test conditions (unless otherwise stated):
Vss = OV
Voo = -16V
Tamb = 25°C
Value
Characteristic
Pin
Supply voltage
Supply current
Input logic level high
low
Output logic level high
low
Analogue output
current range
3
3
5
Min.
Max.
8
14
0
Voo + 3.5
0
Voo+ 0.5
31
14
2,16,18
i
0
-250
11
7
7
7
l.
4
-345
3
400
Conditions
V
rnA
V
V
V
V
8
0
2, 16, 18
1
6
10
Unit
18
-1
Voo
-1
Voo
8, 9, 12-15, 17
Analogue step size
D / A reference, I REF
Oscillator timing
Power clear time
constant
Step time constant
PPM input logic level high
PPM input logic level low
PPM input pulse width
Typ.
50k to Voo
50k to Voo
Iref
3.9k to Voo
Iref
You, < Voo +5V
~A
-455
33k to Voo
C = 22n, R = lOOk See note 1
C = 4.7(.1 R = 100k
kHz
ms
0
-6
22Tosc
Voo
1
C= 470n R = 3.3M
s
V
V
(.Is
2
-1
1
Note 1. Rose. (pin 6) is 25k - 200kQ. lose.::::; O.15C R
/-----(SCREEN
--- --,
18.
68. \
+11V
I i"'
~t-- r~
~';','I~'~
r"--"" 'I
V
T rv'p=1 A
Ii;"
I
I
'~
KODAK
Fln~R
1M
H~
15p
lOR SIMILARl
BOk
*i\'01
RIOOk
m
I_
5L748
SC547
.I'll
,...tm
6'8 P
1M
1M
!
HOp
SAT
VOl
BRI
U
14
16
"
H
-;1o~
~Ok 'f:
41
'
~
f.k
r-' o
4'71:
POWER
TIt
VOL 16
ML922
-'
ON!
STANDBY
toY
Ytr-D
470n
SL490
SAT
/
12 ------O;J.
mt1--r13
14
J9k
15
+--+-+----1--"1"
P,
lSI!
1
ALL
RESISTORS 56k UNLESS OTHfRWISE STATED
Fig. 3 PPM infra-red receiver application with local up/down controls using a directly connected SL490
(Vss= OV).
Supply Voltage Voo
Voltage at any input
Maximum power dissipation
Operating temperature range
Storage temperature range
138
+0.3V to
+0.3V to
600mW
-10°C to
-55'C to
-25V
-25V
+65°C
+125'C
1.
VOO 3
STEP TiC
ABC
12
ABSOLUTE MAXIMUM RATINGS
10;Y-
8'1k
SRI 18
REF~
5 STEP
1
"
hhh"
1-
J
ov
ISk
I.
TDA 2560
ML923
REMOTE CONTROL RECEIVER
The ML923 is an MOS/LSI monolithic integrated circuit
for use as a receiver of remote control signals for television
control. It accepts 24 of the 32 codes transmitted by the
SL490 transmitter circuit in the Pulse Position Modulation
(PPM) method of coding.
PPM
osc. [
1
'--'
Isb Vss
DN,'SB OUTPUT [ 3
RECAll [4
ML923
•
•
•
•
AFC DEFEAT [ 5
STANOBY INPUT [ 6
1 6 Channel Selection Codes
STEP TIME CONSTANT [ 7
Single Analogue Output
MUTE OUTPUT [ 8
Mute Output (Toggle)
On-set Controls-Channel Step, ON, Reset
AtlAlOGUEAEF, [9
•
Normalise to i of Max Output on Analogue Output
•
Outputs Provide Control of ON/STANDBY,
Analogue Mute, and AFC Defeat
•
STEPJNPUT
17P ON INPUT
PPM INPUT [ 2
FEATURES
,.
"
"
"
"n
'0
VOO
:)C
OUTPUTS
0
ANALOGUE OUTPUT
DP18
Fig.1 Pin connections
Choice of Power-Up Function:
a) Power Up to Standby State, Switch to ON
State by Local or Remote Command and
STANDBY by Remote Command.
b) Power Up to ON State, Switch OFF with
Solenoid Operated Mains Switch by Local or
Remote Command.
osc
SHIFT
REGISTER
COMPARATOR
0.
ON liP '••
7_ _ _ _ _ _ _ _ _ _
6
~-~~~~========~-------~--6
1--------,----------0
STAND8YIIPO------------i
RECALL
AFCDEFEAT
0------,------1
STEP liP"
L,.--,,-_j------t-==-------.o
STEP Tie
ON/SBOfP
&------1
'----_ _-69
12
11
C
0
ANALOGUE REF
Fig.2 ML923 block diagram
139
ML923
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
T amb =+25°C, Vss=OV, VDD=-16V
Characteristics
Pin
Supply voltage
Supply current
Input logic level high
Input log ic level low
Output logic level high
1
1
6,17,18
Value
Typ.
Max.
14
18
6
-1
V DD
3,4,11,14 -1.5
Output logic level low
Analogue output current range
Analogue step size
D/A reference, I ref
PPM
Oscillator frequency
On input or standby input time constant for power on
Step time constant
PPM input logic level high ('1 ')
PPM input logic level low ('0')
8
10
10
9
1
60r 17
7
2
2
2
PPM input pulse width
Note 1 Ro," (pin 5) is 47kn - 200kn
Min.
f
0
V DD + 3.5
OV
Units
Conditions
V
mA
V
V
V
50k to V DD
V DD
V DD + 0.5 V
1 Ref 3.9k to V DD
0
"
,
{
1 Ref Vou ,< V DD + 5V
0
-250 -345
-455
mA 33kll to V DD
15
150k
Hz TypicalTC
3k
Hz C=22nFR=100kll
500
ms
250
1
s C = 470nF R = 3.3 Mil
-1
0
V
-6
VDD
V
•
1
•
22 To,"
~s
T=_1_
fosc
~_1_ _
osc-O.15CR
OPERATING NOTES
The receiver operates on a timescale fixed by an internal
oscillator and its external timing components. The oscil·
later may be adjusted to any value behveen 15 Hz and
150kHz (allowing different receivers to respond to different
transmission rates within the same operating area).
A counter is reset whenever a pulse is received and
allowed to count at half the oscillator frequency. For
example, taking an oscillator frequency of 1.56 kHz:Resetting is blocked for the first 14ms and windows
from 14ms to 22ms and from 22ms to 40ms determine
whether a '1' or a '0' is present. Periods between pulses of
40ms to 80ms are recognised as word intervals. Checks
are made to ensure 6 pulses, or 5 bits, are received for a
word to be valid, and only after two consecutive and ident·
ical words is the receiver allowed to respond to the in·
coming code. Channel step time period is derived from an
external time constant.
PIN FUNCTIONS
Positive Logic: Logic '1' = Vss , OV
Logic '0' = VDD , -16V
1. Oscillator Time Constant An RC Time Constant at this
pin defines the internal clock frequency. The clock
frequency may be varied from 15Hz to 150kHz.
2. PPM Input The output of the Front End Amplifier is con·
nected to the pin; the signal must consist of a normal logic
'0' level with pulses to logic '1', corresponding to the PPM
pulse from the transmitter.
3. ON/S8 Output Open drain output. Logic '0' denotes on·
set. Logic '1' standby set. Set to '0' when channel number
changes, and by ON input at logic '0', set to '1' by standby
input or by transmitter selected OFF.
4. Recall OIP Open drain output. A '0' may be used to
trigger an on·screen display. A '0' is output during an input
at pin 17, ON input. The pulse to logic '0' is generated by
any channel change if circuit switches to ON from Standby,
and by recall and normalise commands from the remote
transmitter.
5. AFC OIP Open drain output. A logic '0' can inhibit tuner
AFC. A static output is generated by manual ON control. A
140
pulse is generated by any channel number change.
6. Standby Input A logic '0' will select standby state and
normalise the analogue output to 318 ma.ximum and select
programme 1. An RC time constant may be connected to
select standby at power ON.
7. Channel Step Time Constant An RC time constant
defines the time period between increments of the channel
number when stepping.
8. MUTE Output This will change state (toggle) on receptin
of a Mute command or will remain at logic '1' if the D·A
output is zero. The output is reset by any channel change
command.
9. Analogue Reference A current drain attached to this
input will define the current step of the D·A output. The
current is equal to 8 output current steps.
10. Analogue Output The output of a current mirror D·A
convertor provides a current source of between 0 mA and
1.3 mA. It is variable in 32 steps, UP or DOWN. It is
normalised to 3/8 maximum value by the ON/S8 input, and
by normalise command from the transmitter.
11,12,13,14. Channel Selection Outputs These outputs
encode the 16 channels in binary code.
A
8
C
D
Channel 1
0
0
0
0
Channel 16
1
1
1
1
Set to channel 1 on set switch ON.
15. VDD -14Vto-18Vpowersupply
16. Vss OV (Ground)
17. ON liP A logic '0' will switch the ON/S8 output to ON
(logic '0'). Channel 1 is selected and analogue output is
normalised to 3/8 maximum. An RC time constant may be
connected to select set ON at power on. The AFC defeat
signal is generated and Mute is reset.
18. Step Input The channel code will step up by 1 as long
as the pin is held at logic '0'. The time period between steps
is defined by an RC constant on pin 10. When the channel
code reaches 16 it will go to 1 next step. A step input will
set ON/S8 output to ON and normalise the analogue oL't·
put. Mute is reset if analogue = O.
3:
rID
I\)
Co)
+33V
Note:
1. An output is available to give sound mute during programme switching. With the inclusion of an extra switch on
the transmitter and a transistor in the receiver, remote control of mute is possible.
2. To incorporate accurate fine tuning the addition of a
single transistor provides AFC defeat as long as any local
programme switch is kept depressed.
VARICAPCONTROL
AFe DEfEAT
[
r--r-r
H'---I
p-------c.=1,
ML238
-<---J,
'-,
'-<--"
'~
."
3~k
~
POWERON
11'
CLEAR
17
DATA
READY
OUTPUT
ENABLE
, OUTPUTS
Flg.2 ML924 block diagram
143
ML924
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
VSS = OV; VDD= -16V;Tamb =+25°C
Pin
Characteristic
Supply voltage
Supply current
Input logic level high ('1')
Input logic level low ('0')
Output logic level high ('1')
Output logic level low ('0')
Oscillator frequency
PPM input logic level high ('1')
PPM input logic level low ('0')
Value
Typ.
Min.
9
9
12
3·8,17
-1
VDD
-1
VDD
15
-1
VDD
18
6
10,12·16
1
2
PPM input pulse width
2
1
Power clear time constant
11
1
0
VDD+3.5
OV
VDD+0.5
150k
OV
-6V
3k
Conditions
Units
Max.
22Tosc
V
mA
V
V
50ktoVDD
V
Hz
Typical TC: C= 22nF, R= 100kU
1
T=fosc
s
ms
400
NOTE
•
1
Rose (Pin 1)is56k!lto 150kQ. fosc ~ O.15CR
::;:47.
,)
ov
~'"
-:[
,
.}-
•
3
:~'"
2
•
,
2
11
--{,
r-..
"
--{A
2.2"
"
f---i ' = "~
lS6k
02'*
SUB.
~7
"
.
=~20' ,
.
-{.
--{
.
J .
--{ 7
82,
l)'"
100k
-1
.eo
15
Ml924
DATA
1
14
OUTPUTS
13
--{
"
"r--
--{
lO}-
~.7'
=
;;;
[
)[][ [
ALL56
~ ...
DATAflEADY
Fig.3 Application for receiving 32 codes from SL490 transmitter. Latched outputs.
PIN FUNCTIONS
Positive Logic: Logic '1' = Vss, OV Logic '0' = VOD , 16V
1. Oscillator TC An RC time constant at this pin defines
the internal clock frequency. The clock frequency may be
varied from 15 Hz to 150 kHz.
2. PPM Input The output of the Front End Amplifier is con·
nected to this pin; the signal must consist of a normal logic
'O'level with pulses to logic '1'.
3·8. Control Word Co 10 Cs Six control bits form the
control word which programs the response of the five out·
puts (see Table 1).
144
9. Voo -12V to -18V Power Supply.
10. Data Ready Open drain output. An output of logic '1'
indicates the reception of a valid PPM word. It will remain at
logic '1' for the duration of transmission.
11. Power Clear A capacitor and resistor connected to
this pin define the time delay for the Power Clear Circuil.
12·16. Outputs E·A Open drain outputs which respond to
the PPM input as defined in Table 1.
17. Output Enable A logic '1' will enable outputs A to E. A
logic '0' will turn all outputs off.
18. Vss OV (Ground).
ML924
OPERATING NOTES
live and identical words is the receiver allowed to respond
to the incoming code.
By means of the six control lines, the outputs can res·
pond to the PPM input data in three ways:
1. 5 bit binary output with combinations of latched or
momentary responses as shown in table 1.
The receiver operates on a time scale fixed by an inter·
nal oscillator and its external liming components. The
oscillator may be adjusted to any value between 15Hz and
150kHz (allowing different receivers to respond to different
transmission rates within the same area).
A counter is reset whenever a pulse is received and
allowed to count at half the oscillator frequency. For
example, at an oscillator frequency of 1.5kHz, resetting is
blocked for the first 14ms and windows from 22ms to
40 ms determine whether a '1' or a '0' is present. Periods
between pulses of 40ms to 80ms are recognised as word
intervals. Checks are made to ensure 6 pulses of 5 bits, are
received for a word to be valid, and only after two consecu·
Control Word
CS C4 C3 C2 C1 CO
0
0
0
0
0
0
0
0
0
0
0
1
0
0
0
0
0
0
0
0
0
1
1
1
1
0
0
1
1
1
0
1
1
1
Z
Z
B
A
e
LA
LA
LA
LA
M
M
LA
LA
LA
M
M
M
LA
LA
M
M
M
M
LA
M
M
M
M
M
EIDlclBIA
-
SIR
SIR
SIR
SIR
SIR
SIR
1
1
1
1
LA
LA
LA
LA
LA
M
Z
Z
Z
Z
Z
Z
Z
Z
2
2
2
2
-
SIR
SIR
SIR
SIR
-
LA
M
0
0
1
0
0
1
0
1
1
1
Z
Z
Z
Z
1
1
1
3
3
Interpretation of PPM Words
Output Response
0
C
E
0
1
1
1
1
1
0
0
0
1
1
Z
Z
Control
Mode
2. 4 independant outputs with combinations of latched or
momentary output as shown in table 1. Any output on 1 or 4
receivers can be addressed by each PPM word.
3. The PPM word can be an address or data depending on
the logic state of bit e. If PPM bit e is '0', the remaining four
bits (a, b, c and d) select one of 16 receivers. If bit e is '1',
bits a to d control the outputs A to D. Outputs can be all
latched or all momentary.
M
M
M
M
M
M
L dl
c
Lb I a
PPM decoded
on all outputs
immediately
l
olvlvlzlz
~
~
Output Receiver
address address
{ Resets an SIR
type output
LA
M
LA
M
LA
M
eldlclbla
oLzlzLzJz
~
Address Receiver
mode
address
l
11vlvlzlz
--..- --..-
,~"'"
0" .,"' address
address
Sets an SIR type
1momentary
output or pulses a
output
-!.-/o/cIB/A
Data PPM data sent
mode to outputs of
addressed
receiver
Table 1
NOTES:
1. Control Mode 1: Direct Response to the PPM Code
2. Control Mode 2: ZZ is a 2 bit address for the receiver
YY selects one of 4 outputs
VY
OUTPUT
00
01
10
11
A
B
c
D
3. Control Mode 3: ZZZZ is a4 bit address that selects, by which of 16PPM codes a receiver will be selected,
If PPM bit e = '1', the rest of that PPM word will be read as data. If PPM bit e = '0' the rest olthat PPM word will be
read as an address.
ABSOLUTE MAXIMUM RATINGS
VDD supply and all inputs wrt VSS
Storage temperatures
Operating temperature ambient
+0.3V to -25V
- 55°C to + 125°C
-10°C to +65°C
145
ML924
[
,
~
I
~
]
[
l'
[
,
~
[
[
~
I
P,
[
v"
V.
[
Ml924
Ml924
ROCKWELL
ROCKWELL
R6520PIA
PPS4I1
OR
MOTOROLA
MC&820
[
P
P
DATA
~
DATA
-
_1>17
PM
[[ -
P",
d [
V.
I
-
P.
l
J"
J"
NOTE, USE PERIPHERAL INTERFACE B OR PERIPHERAL
~
Ifa
PORT B ONLY
rP,
[
1-
,
~
I
~
V..
V"
P10lP20
RA,
[
.,
ML924
ML924
INTEL
MC&48
PJC1650
FAMILY
V.
V"
L--_-'
DATA
READY
-RA'
) l[[
- ..'_"_.....:.V.I-._
I
Flg.4 Inter/ace to commonly used microprocessors
146
V..
) [[,'
r--
P11128
~ '171'27
V••
I
ML925
REMOTE CONTROL RECEIVER FOR TOYS
The ML925 is an MOS/LSI integrated circuit for use as a
decoder of PPM remote control commands transmitted by
the SL490 or SL491 circuit. It is designed to control either a
toy vehicle with two-speed drive motor and a three position
latching steering system, or a vehicle with momentary action steering and a third motor, typically a winch. This
second vehicle type also has four selectable speeds. Both
types have horn, headlights, hazard flasher and turn indio
cator facilities.
The circuit can operate on the first set of 16 SL490
commands or the second set of 16, thus giving simul·
taneous control of two independent vehicles with the same
integrated circuit type in both.
'-"
-VOD [ ,
PPM TIC [ 2
"P+f
16P
_ MOTOR 3
PPM I,'? [ 3
HAZARD [ 4
15
ML925
fLASHER [ 5
14
Multifunction Toy Control
High Power, Free Drain Buffers on all Outputs
•
Uses Weil-Proven High Security PPM Coding
with Double Word Checking
•
Minimum Component Interfaces Required to
Motors and Lamps
•
Direct Connection to SL480 Infra-red Preamplifier
P
P
SElECT CODESH
mOBACK (MOTOR 21
13P LIGHTS
12P SElEcrTYPE
SPfEIlT!C [ 6
+VSS [ 7
"p +1 MorOR2
lOP -
M01OR{ ~:
FEATURES
•
•
lap HORN
OPtS
Fig.1 Pin connections
ABSOLUTE MAXIMUM RATINGS
Voo supply inputs with respectto Vss +O.3V to-25V
Storage temperature
- 55°C to + 125°C
Operating ambient temperature
-10°C to + 65°C
1-_________-02
PPM
o~~~c
lIP
7
4 - - - - 0 +V,..
~~~"c~-----~r---~~----~::::::::::::::~----~
HORN
TYPE
OECODER
HAZARD
~:~~~~1Z
,,'-------1
TYPE
FEEDBACK
FLASHER
(MOTOR2)
,
-v",,~
MOTOR 1
MOTOR 2
MOTOR 3
(DRIVE)
(STEERING)
(WINCH)
Fig.2 ML925 block diagram
147
ML925
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated):
Tamb = +25°C, Vss= OV, Voo = -15V
Characteristic
Pin
Supply voltage, Voo
Supply current
PPM input high
low
Code or type select high
low
Steering feedback, speed time
Constant threshold
Output voltage motor drives
other drives
-12
1
1
-1
3
3
Voo
12,15 -1
12,15 Voo
6,14 -2.5
-15
8
8·11
16, 17
4,5
13, 18
Output leakage all outputs
PPM oscillator frequency
2
Speed control oscillator
Flasher rate
PPM input pulse width
6
5
3
E
X
X
X
X
X
X
X
X
X
X
X
X
X
X
X
X
TRANSMITTER CODES
C
B
D
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
1
i
0
0
1
1
0
0
1
1
0
0
1
1
Value
Units
Min. Typ. Max.
-3
-18
12
0
-6
0
-10
-3.5
V
mA
V
V
V
V
V
-0.2
-0.5
V
Output current = 10mA
-0.2
-0.5
V
Output current = 5mA
1
150k
Jl.A
Hz
kHz
Hz
Hz
Output voltage = -15V
15
4
50
0.8
1
Conditions
22T
Jl.S
C = 33nF, R = 50kfl
Rpos = 120k, Rne , = 270kfl, C = 100nF
For pin 6 as above
T= 1/1 at pin 2
VEHICLE TYPE
A
TYPE A, 'CAR'
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
STOP
FORWARD STRAIGHT
REVERSE STRAIGHT
HORN (MOMENTARY)
NOT USED
FORWARD LEFT
REVERSE LEFT
FLASHER ON/OFF
NOT USED
FORWARD RIGHT
REVERSE RIGHT
LlG HT ON/OFF
SPEED 1
SPEED 1
SPEED 2
SPEED2
TYPE B, 'TRUCK'
STOP
FORWARD
REVERSE
HORN (MOMENTARY)
NOT USED
STEER LEFT (MOMENTARY)
'WINCH IN' (MOMENTARY)
FLASHER ON/OFF
NOT USED
STEER RIGHT (MOM ENTARY)
'WINCH OUT' (MOMENTARY)
LIGHTS ON/OFF
SPEED 1
SPEED 2
SPEED 3
SPEED 4
Table1 Decoderresponse to PPM codes
CIRCUIT DESCRIPTION
OPERATING NOTES
The decoder operates on a timescale fixed by an inter·
nal oscillator and its external timing components. The
oscillator may be adjusted to a wide range of frequencies
to allow different decoders to respond to different PPM
rates. PPM words consist of six narrow pulses separated by
5 gaps, a short gap for a '1' and a long gap for a '0', in the
ratio 2 to 3. Words are separated by a gap of ratio 6. Two
complete correct adjacent words are required belore the
decoder will respond.
A second on·chip oscillator provides a frequency which
sets the mark/space ratio of the motor speed control and
hazard and indicator flasher rate. A power·on reset is also
provided during initial power·up.
Simultaneous control of two independent vehicles is
possible. For one vehicle the first bit of the 5·bit trans·
mitted code is a '0' and for the second vehicle the first bit is
a '1' as shown in Table 1.
1. In Table 1, X determines one of two vehicles to be con·
trolled by independent controllers within the same area.
The same decoder design can drive either vehicle. X = 0 for
vehicle 1, X = 1 for vehicle 2.
2. Momentary controls only give an output for the duration
of a PPM command stream, i.e. for as long as a transmitter
button is depressed.
3. Hazard and lights control codes provide a toggle action;
push once for on, push again for off. There is an internal
time·out within the decoder to cater for interruptions in the
PPM stream by noise.
4. Vehicle type A will drive at half or full speed and has a
latching drive. The steering has three positions: hard left,
centre and hard right and is driven momentarily during
code transmission. The centre position may be indicated
by a contact running on a conductive track attached to the
steering bar (see fig A). The track should have a non·
148
ML925
conducting section at the centre and the two halves should
be taken to Vss and Voo respectively. The contact, which
should be fixed to the body of the vehicle, is attached to a
pin on the decoder and a two resistor bias network. The
contact must not conduct with either area when in the
centre position.
5. Vehicle type B also has a latched drive direction, which
remains latched until STOP is pressed; but its steering is
momentary, so that it will progress left (say) until the com·
mand is removed, and stay in that position until a further
steering command is received. This provides a time·
proportional sieering system.
6. Vehicle type B has four possible drive speeds; quarter,
half, three-quarters and full speed. From STOP or power·on
the speed selected is quarter, or speed 1. Further speeds
are selected by the four latched speed select commands.
The steering speed or rate of progression is proportional to
the drive speed.
7. Vehicle type B has provision for single speed driving of a
third motor (forward or reverse). Control of this motor is
momentary, stopping when commands cease to be trans·
mitted.
8. One output of the decoder provides a continuous flash·
ing signal. This can be gated with various other outputs of
the decoder (using simple transistor gates) to give auto·
matic flashing lights or buzzers when functions are oper·
ating. Examples are: left and right turn indicators, buzzer
when reversing, warning lamp when winch in operation or
siren switched on and off by 'lights' command.
HORN
BC237
i-
BC~,;
-- --
I
I
I
I
I
I
I
BC237
-6'1
:
L _______ --'
TYPICAL MOTOR DRIVE
o----------{
Bell7
LIGHTS
-.v
Fig.3 Infra·red control for car or truck
PIN FUNCTIONS
1. VDD
-12V to -18V power supply.
2. Oscillator time constant
An RC time constant of a capacitor to Vss and a resistor
to Voo defines the internal clock frequency for demodul·
ating PPM.
PlESSEY
ML825
3. PPM Input
The output of the 'front end' amplifier is connected
here; the signal must be a normally low level of - 6V, and
have PPM pulses going positive to -1 V.
4. Hazard
An open drain output to drive a flashing lamp or buzzer
at a rate determined by pin 6 time constant. Toggled on or
off by a single PPM code.
5. Indicator signals
A permanently pulsing output at a rate determined by
pin 6 time constant. Open drain drive.
Fig.4 Infra·red control for vehicle with 3·position steering
6. Speed time constant and power-on reset
A capacitor and resistor to Voo and a resistor to Vss de·
fine the frequency of the motor speed control pulses and
the warning and indicator pulses.
149
ML925
7. V. s
OV power supply.
8. Forward
Open drain high power latched drive to the drive motor
circuit. When on, the drive motor should move the vehicle
forward.
9. Reverse
Open drain high power latched drive to the drive motor
circuit. When on, the drive motor should move the vehicle
in reverse.
10. Steer left
Open drain high power drive to the steering motor cir·
cuit. When on, the steering should move on the left.
11. Steer right
Open drain high power drive to the steering motor cir·
cuit. When on, the steering should move to the right.
12. Vehicle type
An input to determine the type of vehicle and the inter·
pretation of control codes. Vss selects Type A (car) V00
selects type B (truck).
13. Lights
Open drain output to drive headlights etc. Toggled on or
off by a single PPM code.
14. Steering
An input from the centre contact of the steering feed·
back system for vehicle type A. A resistor to Vss and a
resistor to Voo are required as a bias chain.
15. Code set
An input to determine which set of 16 PPM codes the
decoder responds to. Voo will select the first 16 (E = 0) and
Vss will select the last 16 (E = 1).
16. Third motor +
Open drain high power drive to a third motor circuit for
vehicle type B.
17. Third motorOpen drain high power drive to a third motor circuit for
vehicle type B. Drives motor in opposite direction to pin 16.
18. Horn
Open drain output to drive a horn or buzzer. A momen·
tary output selected by one PPM code.
Operation of the various functions is described more fully
in 'operation' and in Table 1.
150
Ml926/7
REMOTE CONTROL RECEIVERS
(With Momentary Outputs)
The ML926 and ML927 are MOS LSI monolithic circuits
for use as receivers of remote control signals for television
control and many other applications. They are general purpose devices each receiving sixteen of the thirty-two codes
transmitted by the SL490 circuit as pulse position modulation (PPM).
-voo('o OSCILLATOR TIME CONSTANT [ 2
PPM INPUT [3
ML
926/7
80)
7
C
MOMENTARY
6
AB
BINARY OUTPUTS
+Vss [4
~---'
UPS
Fig. 1 Pin connections
FEATURES
•
•
Minimum Package Size
8-Lead Minidip
Four Outputs Indicate in Binary the Code
Currently Being Received, and Are Switched Off
(Low) When No Valid Code is Detected.
•
•
On-Chip Oscillator
High Power, Free Drain, Output Buffers
OPERATING NOTES
The receiver operates on a timescale fixed by an
internal oscillator and its external timing components. The
oscillator may be adjusted to any value between 15Hz and
150kHz (allowing different receivers to respond to different transmission rates within the same area) .
A counter is reset whenever a pulse is received, and
allowed to count at half the oscillator frequency. For
example, take an oscillator frequency of 1.5kHz:Resetting is blocked for the first 14 ms and windows from
14ms to 22ms and from 22ms to 40ms determine whether a
'1' or a '0' is present. Periods between pulses of 40ms to
BOms are recognised as word intervals. Checks are made to
ensure 6 pulses, or 5 bits, are received for a word to be
valid, and only after two consecutive and identical words is
the receiver allowed to respond to the incoming code.
The ML926 responds only to codes 00001 to 01111
from the SL490 transmitter whereas the ML927 responds
to codes 10001 to 11111,
Fig 2 Block diagram
PPM INPUTS
5
,
VDD supply and inputs w.r.!. Vss
Storage temperature
Operating temperature ambient
+0.3Vto-25V
-55'C to + 125'C
-10'C to +65°C
-5'1 LOGIC 1
,---6
ABSOLUTE MAXIMUM RATINGS
{.,V LOGIC 0
4
3f!- ~
,
!2'n
[ [ UJAL;~
6
'100
-"
'Iss
ov
Fig. 3 Test cirCUit
151
ML926/7
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated):
Voo = -16V
Tamb
=
25'C
Characteristic
Pin
Operating supply voltage range
Current consumption
1
12
2
3
3
3
-1
Voo
1
2
15
PPM input
Input logic level high
Input logic level low
Input pulse width
Min.
Value
Typ.
Max.
14
3
18
4
0
-6
22Tosc
Units
Conditions
V
mA
V
V
"sec
1
T=~
Oscillator time constant See Note 1
Oscillator frequency
Variation wrt Voo
Output voltage high
Output device leakage (Output OFF)
Note 1. Rose (Pin 2) is 47kn -+ 200ko . losc
~
5-8
5-8
3k
150k
Hz
Hz
1
%N
-1.5
V
j.lA
0
1
Typical TC: 22nF toVss
100k to Voo
Rl = 3.0K to VDD
0.1 ~CR
PIN FUNCTIONS
Momentary binary outputs
1. Voo
-14V to -18V power supply
2.
Oscillator time constant
An RC time constant of a capacitor and resistor at this
pin defines the internal clock frequency. The clock
frequency may be varied from 15Hz to 150kHz.
3.
PPM input
The output of the 'front end' amplifier is connected to this
pin; the signal must consist of a normal logic 'Iow' level with
pulses to logic 'high' corresponding to the PPM pulses from
the transmitter.
4. Vss
OV (ground)
5-8. A.B.C.D
Four open drain high power transistors give a binary
coded output of the valid code being received.
I
Transmitter
Code
ML926
ML927
EDCBA
DCBA
DCBA
o0 0 0 0
o0 0 0 1
00010
o0 0 1 1
000
o0 0
001
001
o1 0
o1 0
o1 1
o1 1
1 0 0
1 0 0
1 0 1
1 0 1
1 1 0
1 1 0
1 1 1
1 1 1
o0 0
o0
00100
00101
00110
o0 1 1 1
o 1 000
o1 0 0 1
o 1 010
o1 0 1 1
o1 1 0 0
o1 1 0 1
o1 1 1 0
o1 1 1 1
1 0 0 0 0
1 0 0 0 1
1 0 0 1 0
1 0 0 1 1
1 0 1 0 0
1 0 1 0 1
1 0 1 1 0
1 0 1 1 1
1 1 0 0 0
1 1 0 0 1
1 1 0 1 0
1 1 0 1 1
1 1 1 0 0
1 1 1 0 1
1 1 1 1 0
1 1 1 1 1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
o 000
o0 0 1
001 0
o0 1 1
o1 0 0
o1 0 1
o1 1 0
o1 1 1
1
1
1
1
1
1
1
1
Table 1 Response to SL490 codes
152
0 0
0 0 0
0 0 1
0 1 0
0 1 1
1 0 0
1 0 1
1 1 0
1 1 1
ML928/9
REMOTE CONTROL RECEIVERS
(WITH LATCHED OUTPUTS)
Plessey Semiconductors have developed and produced a range of monolithic integrated circuits which
give a wide variety of remote control facilities. As well
as ultrasonic or infra-red transmission, cable, radio or
telephone links may also be utilised. Pulse position
modulation (PPM) is used with or without carrier and
automatic error detection is also incorporated. Although
initially designed with TV remote control in mind the
devices may equally easily be applied for use in radios,
tuners, tape and record decks, lamps and lighting, toys
and models, industrial control and monitoring.
The ML928 and ML929 are general purpose remote
control receivers, each receiving and latching 16 of the
32 codes transmitted by the SL490 circuit in the PPM
(Pulse Position Modulation) mode. The ML928
responds to codes 00000 to 01111 only, and the
M L929 to codes 10000 to 11111. Both devices are
packaged in 8-lead minidip to minimise board area.
The on-chip oscillator may be adjusted from 15Hz to
150kHz, allowing different transmission rates. They
have a high degree of immunity to incorrect codes;
there must be two consecutive correct codes received
before the outputs can change.
Ie
'-"
8
OSCILLATOR TIME CONSTANT
Vee (ev)
2
PPM INPUT
3
ML
92819
5
I
: ) LATCHED
BINARY
B OUTPUT
Vssj16'J) . '_ _ _... '
DP8
Fig. 1 Pin connections
FEATURES
•
•
•
•
•
•
Accepts 5 Bit PPM
On-Chip Oscillator, 15Hz to 150kHz
Range
Easily Used With Ultrasonic, Infra-Red
or Other Transmission Media
Four High Drive Outputs
16 Latched States
Minimum Sized Package
Fig. 2 ML928, ML929 remote control receivers block diagram
QUICK REFERENCE DATA
•
•
•
•
•
Power Supply: 12V to 18V. Typical 4mA
at 16V.
Demodulation: Pulse position with time
window checking by on-chip oscillator
Decoder: 5 Bit with successive codeword
comparison
Outputs: Maximum 15mA sourced from
open drain drive
Logic convention: Logic 0 - output
transistor ON, pulls
output to V ss
Log ic 1 - output
transistor OFF
PPM INPUTS
{-lV lOGIC 1
-6'01 lOGIC 0
,--,
4
'P-- 1 ,ill-,~
7'
6
7
8
2
]",,:,""
~
lJ
~
II
/21"
1""""\.1
6
Vco Vss
-16
0'01
Fig. 3 Test circuit
153
ML92S/9
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Vss = OV
Vee = -16V
Tamb = +25'C
Value
Characteristic
Pin
Current Consumption Vee
Supply voltage
1
1
PPM input
Logic '0' level
Logic '1' level
3
Input pulse width
Typ.
Max.
3
4
-12
5
-18
mA
V
-1
Voe
0
-6
V
V
1
Oscillator Timing
Frequency
22To5O
I'S
150k
Hz
Hz
Conditions
1
Tosc= ~
2
15
4k
Variation w.r.t. Vee
Latched binary output
Logic '0' output voltage
Units
Min.
1
5, 6, 7, 8
-1.5
DV
Output leakage in logic
'1' state
1
%/V.
V
Typical TC : 22 nF to Vss,
1DDkfl to Vee
RL = 3.Dk to VDD
I'A
~r
""::::""3V
-.v
Fig. 4 Forward and reverse drive of two small DC motors
PIN FUNCTIONS
Negative logic: '0' is OV (V ss), '1' is - 12V
to -18V (V eo)
1. Veo
-12V to -18V power supply
2.
Oscillator time constant
An R-C time constant at this pin defines the internal
clock frequency. The clock frequency may be varied
from 15Hz at 150Hz and should be set so that there are
40 periods in one 'to' transmitter pulse interval.
154
3 .. PPM input
The output ofthe 'front end' amplifier is connected
to this pin; the signal must consist of a normal logic '1'
level with pulses to logic '0' corresponding to the PPM
pulses from the transmitter.
4.
Vss
OV (ground)
5-8. A,a.C.D
Four open-drain high power transistors give a binary
coded latched output of the last valid code received.
ML928/9
Latched binary outputs
680
Transmitter
Code
ML928
ML929
EDCBA
DCBA
DCBA
o0
o0
000 0
o0 0 1
001 0
o0 1 1
o1 0 0
o1 0 1
o1 1 0
o1 1 1
1 0 0 0
1 0 0 1
1 0 1 0
1 0 1 1
1 100
1 1 0 1
1 1 1 0
1 1 1 1
0 0 0
0 0 1
00010
00011
00100
o0 1 0 1
00110
o0 1 1 1
o 1 000
o1 0 0 1
o 1 010
o1 0 1 1
o 1 100
o1 1 0 1
o1 1 1 0
o1 1 1 1
1 000 0
1 0 0 0 1
10010
1 0 0 1 1
1 0 1 0 0
1 0 1 0 1
1 0 1 1 0
1 0 1 1 1
1 1 0 0 0
1 1 0 0 1
1 1 0 1 0
1 1 0 1 1
1 1 1 0 0
1 1 1 0 1
1 1 1 1 0
1 1 1 1 1
No change
sJ:
+16IJo-+-4-~_ _
No change
Fig. 5 Direct drive of LEOs
ABSOLUTE MAXIMUM RATINGS
o0 0
o0 0
001
o0 1
o1 0
o10
o1 1
o1 1
1
1
1
1
1
1
1
1
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
Voo supply and inputs w.r.t. Vss
Storage temperature
Operating temperature ambient
+O.3V to -25V
-55'C to + 1 25'C
-10'C to +65'C
Table 1 Response to SL490 codes
155
156
SL470
BCDT01 OF10 DECODER/VARICAP DRIVER
FEATURES
•
•
•
•
•
•
•
Up To 10 Programmes
Direct Varicap Voltage Selection
TIL Level Compatible Inputs
May be Directly Driven by ML920
Series Receivers
Low Component Count
Low Cost
Can Be Used To Drive Indicators
ov
,
IBPO/PS
DIP 6
1
15P O/P4
O/P7
3
14PO/P3
O/PS
• SL470 " PO/P2
DIPS
5
DIP 10
G
npvC(
lira
J
IOPI/PA
IIPC
B
9bl/PB
12PO/Pl
DP16
Fig. 1 Pm connections
----~I------------------~11vcc
QUICK REFERENCE DATA
•
•
•
•
+
Power supply 33V 3mA
lout of 10 outputs selected high
Output drive 2mA
Input 4 Bit BCD, TIL compatible
0(23 )
C(22)
0
0
0
0
0
0
0
0
1
1
0
0
0
0
1
1
1
1
0
0
8(21)
0
0
1
1
0
0
1
1
0
0
A(20)
~I~O/p
ii~1
EiCii~2
C~3
c~:
alP (high)
0
1
0
1
0
1
0
1
0
1
DC
B~
1
2
3
C~4
C~5
C~8
C~7
4
6~~8
5
6
7
8
O~9
-.~
----l'
ov'--'
9
O~10
10
Fig, 2 Logic diagram
Table 1 Decode table
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Tamb = 25°C
Vee = 33V
Characteristic
Operating supply voltage
Supply current
Selected output level
Unselected output
levels
Input high state
Input low state
Input current
Value
Pin
Min.
Typ,
11
11
2-6,12-16
30
36
3
Vce - 1.5
2-6,12-16
7-10
7-10
7-10
0.5
1.7
-0.3
Max.
Units
6
Vcc-3.5
V
rnA
V
5
+0.4
1.5
V
V
V
mA
Conditions
O/Ps unloaded
lOUT = 2mA
100k load to OV
V;n = 1.7V
157
SL470
Ml920
ML922
ML923
ML928
SL470
ML929
9
10
11
12
13
3·.
k
3·9k
.33V
!VAFUCAP SUPPL.V}
Fig.3 Typical application circuit for 8 programmes
7 SEG DRIVER
I
1
;0
I
AMP
SELECTOR
RX
I
I
Lis I
VARICAP
CONTROL
e • go
'invertersmayberequir&c!insomeappilcalions
LOCAL TX
Fig. 4 Complete remote control system
ABSOLUTE MAXIMUM RATINGS
Storage temperature
Operating temperature
Supply voltage
158
-55°C to +125°C
_10°C to +65°C
36V
SL480
INFRA-RED PULSE PRE-AMPLIFIER
The SL480 is a bipolar integrated circuit containing
three amplifier stages. Its output is directly compatible
with the M L920 range of remote control receiver
circuits. It is packaged in an 8-lead plastic package. The
gain of the amplifier stages may be adjusted to suit the
application. The input impedance is approximately 20 Mil.
STAGE 30[CQUPtE
rv-ap
SL480
STAGE 2 DECOUPLE
1 ~ STAGE 1 DECOUPLE
OUTPUT
2
.16V
J
C
PHOTOOIOOE INPUT [ 4
5
P0'1
NO I U~tU
DPB
FEATURES
•
•
•
•
Minimum Component Solution to InfraRed Detection
Adjustable Gain
Directly Compatible With Plessey ML920
Range of Receivers
May Be Used As A General Purpose 100 kHz
Fig. 1 Pin connections
Limiting Amplifier
ABSOLUTE MAXIMUM RATINGS
Supply,Vcc
Maximum power dissipation
Operating temperature range
Storage temperature range
20V
480mW
_lOoe to +65°e
-55°e to +125°e
INPUT
OUTPUT
T.
OECOUPLING
Fig. 2 SL480 block diagram
159
SL480
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
T.mb = 25°C
Vcc = +15V
Characteristic
Value
Pin
Min.
Operating voltage range
Supply current
Open loop gain
Input impedance
Output current sink
Internal pullup resistor
Quiescent OIP voltage (low)
Pulse output (high)
Units
Typ.
18
4
12
3
3
4,2
4
2
2
2
2
9
15.5
Conditions
Max.
1.5
100
20
100
50
11
V
mA
dB
MO
Sum of 3 stage gains
~A
kO
V
V
At reduced gain
No load
OPERATING NOTES
An external resistor of, typically, 330k 0 between
pins 4 and 3 provides current for the photo detector
diode connected across pins 4 and 6. Any voltage
generated across the diode by incident light is amplified.
The gain of each stage may be readily adjusted
by external resistors in series with decoupling capacitors between pins 7, 8 or 1 and ground. For maximum gain the resistors are dispensed with except at
pin 8.
Typical decoupling capacitors are 22nF. The output
goes high towards Vcc when light is detected. This is
compatible with the PPM input of the ML920 series of
remote control receivers. The SL480 is compatible with
the full 'power supply range of the ML920 series and
can also be used at a lower supply voltage as long
as Vcc is common to Vss of the MOS device, i.e.
common posiiive.
COMMON
560
ov--+-C=l---''--{]
SL480
" -_ _ _ TO INPUT OF
ML920 SERIES
ADJUST
GAIN
The circuit diagram of the SL480 infra·red pulse ampli·
fier is shown in Fig.5. Pulses generated by an infra·red
receiver diode are amplified to a suitable level for direct
connection to the input of any of the Plessey Semi·
conductors ML900 series of remote control receiver cir·
cuits.
For basic operation, the receiving diode and SL480 in·
put is biased with a single resistor to the positive supply.
Any infra·red light reaching the diode generates a leakage
current which causes a voltage drop across the bias
resistor.
The SL480 input stage consists of a compound emitter
follower (TRl and TR2) which provides a high input impe·
dance and allows a relatively high diode load resistor as
well as a voltage drop of around 1.3V between the input
and the bases of the first amplifier stage (TR6, TR1).
Transistors TR6 and TRl form a differential amplifier
which is designed to prevent low frequency or DC input sig·
nals from reaching subsequent stages of the amplifier.
Since the bases of transistors TR6 and TRl are internally
connected by the 6.3k resistor R3, low frequency signals
are applied to both sides simultaneously causing no
change in collector current and therefore no output to the
second stage. Higher frequency signals are amplified
because TRl base is decoupled externally on pin 1.
Stage 2 gain is provided by a similar differential ampli·
fier to stage 1 except that the relatively stable DC input volt·
age provided by stage 1 output allows the use of a tail resis·
tor Rll rather than a current source. Decoupling of AC sig·
nals is provided at pin 8.
Fig.3 Gain adjustment, common positive
82p
ABC
68,
FigA Compact infra·red receiver
160
P
SL480
019
52k
'"
OlP2
Fig.5 SL480 circuit diagram
Stage 3 is similar to stage 1, but with an extra current
mirror (TR24 to TR26) to provide signal inversion at the out·
put.
The standing current through the output load resistor
and thus the output voltage, is set by the current in R15.
This current willamount to about 100I'A, and give an out·
put voltage about 5V below the positive rail with a 15V
supply.
'.
It should be noted that there is a parasitic zener diode of
about 6V in parallel with the output load resistor R19; this
diode will be destroyed if the output is shorted to the nega·
tlve supply rail. Stage 3 decoupling is provided at pin 1.
With a 15V supply, the input stage will operate with in·
put voltages ranging from 15 V down to 5V. This will allow
the device to function satisfactorily in high ambient light
conditions which produce high leakage currents In the
receiving diode. A single transistor circuit Is shown in Flg.6,
which prevents the input voltage to the SL480 changing for
diode leakage currents up to several milliamps. By careful
choice of Rand C values, this circuit can be made to give
extra rejection of low frequency modulation such as that
.
produced by incandescent lamps.
Under conditions of very high ambient light the circuit
may show signs of instability. This can be prevented by
connecting a 2.2k resistor In series with the transistor
emitter.
If required, the gain of each stage of the SL480 can be
set individually by connecting a resistor in series with the
decoupllng capacitor. A 6k resistor will reduce the stage
gain to half its full value of about 40dB. Normally it is only
necessary to reduce the gain of the second stage with
about 33-56 k.
If preferred the decoupling components on pins 1, 7 and
8 can be earthed to the negative supply on pin 6.
As with any high gain device, care is needed in the lay·
out of printed circuit boards to prevent instability. All de·
coupling and input components should be mounted close
to the SL480. A suitable printed circuit layout for the SL480
is shown below.
Decoupling of the power supplies local to the SL480 is
advisable. A resistor of about 5600hms in series with the
negative rail and a parallel capacitor of 68microfarads
being adequate (see Fig.6),
The decoupling resistor should always be in the nega·
tive supply as the ML920 series remote control circuits
have a threshold close to the positive rail, and any voltage
drop here would reduce the noise immunity.
OUTPUT
+
CD
<:
I] n
c'=i=
TRl
01
01
C6
-U:
.
~I-C3
~I SL4809 :;:C2
Fig.6 Typical infra·red amplifier application with improved
detector biasing
161
162
SL490
REMOTE CONTROL TRANSMITTER
Plessey Semiconductors have developed and produced a range of monolithic integrated circuits which
give a wide variety of remote control facilities. As well
as ultrasonic or infra red transmission, cable, radio or
telephone links may also be utilised. Pulse position
modulation (PPM) is used with or without carrier and
automatic error detection is also incorporated. Although
initially designed with TV remote control in mind the
devices may equally easily be applied for use in radios,
tuners, tape and record decks, lamps and lighting, toys
and models, industrial control and monitoring.
The SL490 is an easily extendable, 32 command,
pulse position modulation transmitter drawing negligible
standby current. It may be used with the M L920 series
of remote control receivers.
OVAND xxxoo
SELECTION
c~~;~~
SOURCES
I[
r:
OUTPUT
-
,
100XX [
CARRIER TIME CONSTANT
"P
"
STABILISER VOLTAGE
3
"
~ PPM TIME CONSTANT
B
~ XXXO'I
P
" P,ll"l
P
9
"
4
"
, SL490"
COIXX [ £
OlOXX [
OllXX [
~
2
,
"
XXXII
lIDXX
b
101XX
SINKS
SELECTION MATRIX
CURRENT
SOURCES
DP18
Fig. 1 Pin connections
FEATURES
QUICK REFERENCE DATA
II
..
II
II
Ultrasonic or Infra-red Transmission
Direct Drive for Ultransonic Transducer
Direct Drive of Visible LED When Using
Infra-red
II Very Low Power Requirements
II Pulse Position Modulation Gives
Excellent Immunity From Noise and
Multipath Reflections
II Single Pole Key Matrix
II Switch Resistance Up To 1 kG Tolerated
II Few External Components
II Anti-Bounce Circuitry On Chip
,mcnON MATRIX
XXXIO CURRENT
"
•
•
•
•
•
Power Supply: 9V, Standby 6f1A
Operating 8mA
Modulation: Pulse Position With or
Without Carrier
Coding: 5 Bit Word Giving a Primary
Command Set of 32 Commands
Key Entry: 8 X 4 Single Pole Key Matrix
Date Rate: Selectable 1 Bit/Sec to
10k Bit/Sec.
Carrier Frequency: Selectable OHz (no
carrier) to 200KHz.
v[(
t-~--~---< VREG
SWITCH
MA.TRIX
CURRENT
SOURCES
ENCODER
[ODE
REGISTER
'}OUTPUT
1
TO TOR
TIf.4E CONST
Fig. 2 SL490 transmitter block diagram
163
Sl490
ELECTRICAL CHARACTERISTICS (see Fig.3)
Test conditions (unless otherwise stated):
Tamb = 25'C
fe = 40kHz
Vee = +7Vto+9.5V tl = 18ms
Value
Characteristic
Pin
Operating supply current
Standby supply current
Stablised voltage
Output current available
Output voltage swing
Output current
External switch resistance
External switch closure time
External carrier oscillator resistor
required, R2
External PPM resistor Rl required
Ratio to/tl
Pulse width, t p
I nter word gap, t g
Varialion of 10 wilh Vee
10 wilh Vee = 9.5V 10 wilh Vee = 7.5V
Pulse width To
Inler word gap 10
4
4
Typ.
Max.
8
17
17
2,3
2,3
4.3
4.6
16
30
4.9
1
18
16
2,3
2, 3
2,3
20
15
1.4
2
50
2,3
2,3
2,3
0.96
2
50
54
1
Vec
mA
Conditions
Vcc
=
9.5V
~A
V
mA
V
mA
kO
ms
40
30
1.5
3
54
80
60
1.6
4
58
kO
kO
3
1.04
4
58
6
Unloaded
Peak value
C2 = 680pF
Cl = 0.681lF
ms
ms
ms
ms
t,
ir
"I
Units
5
1
t,
to
I"" T
Min.
Fig.3 PPM word notation
BA
SA
SA
SA
00
01
10
11
ED[
000
00<
0'0
011
:~
'0
'0'
11
"
7
6
13
14
(l
.A
°NJ!
"fO'
1::" r"> ~.
Rl
SL 490
5
15
4P--t9V
"
3
"
2
"~'~
~2
Fig. 4 Test and ultraso.nic application circuit
164
TOR
~-
to "" 1.4. C1. R1
1
iC,,"O.7 C2. R2
SL490
8x4
KEYPAD
g--.r
10
11
12
13
SL490
"
15
TR'
80437
PP3
'l
'l
2 x:CQV99
OR
1x CaX47
Fig.S Infra·red application circuit
OPERATING NOTES
Fig.5 shows the circuit for a simple infra·red transmitter
where the PPM output from pin 2 of the SL490 is fed to the
base of the PNP transmitter TR1, producing an amplified
current pulse about 151'sec wide. This pulse is further amp·
lified by TR2 and applied to the infra-red diodes 01 and 02.
The current in the diodes and the infra-red output is control/ed by the quantity, type, and connection method of the
diodes and also by the gain at high currents of the transistors.
The most common solution where cost is important is
to use 2 single-chip diodes, such as the CQY99 connected
in series.
Improved output can be obtained by using four CQY99
diodes in a series paral/el arrangement, but it is usual/y simpler to use 2 multichip diodes such as the CQX47 connected in paral/el or a single CQX19 which gives similar
results.
A significant increase in range can be obtained by using
diodes such as the CQY99 in conjunction with a plated
plastic parabol ic reflector.
When building the transmitter, care should be taken
with the choice of the capacitor C2 and with the circuit layout, particularly when multi-chip diodes are being used, as
the current pulses can be as high as 6 to 8Amps.
Transistor choice is also important and any substitutes
should have high current gain characteristics and switching speeds similar to those specified in Fig.3.
An increase in output can be obtained by connecting
TR2 in common emitter configuration, but care should be
taken not to exceed the rating of the diodes.
Choice of PPM Frequencies
Although the ML920 series of remote control receivers
is designed to work over a wide range of PPM frequencies,
the actual usable range may be restricted by the application. The analogue outputs on the ML920, ML922 and
ML923 serve as a good example, since the outputs wil/
step up or down, one step for each pair of PPM words
received. This in turn fixes the rate of increment or decrement of the volume or colour controls of a TV set.
When the transmitter is being used with an infra-red
link, with high current pulses fed to the diodes as in Fig.5,
power consumption wil/ increase with frequency. It is thus
advisable that with a battery power supply, the slowest
PPM rate consistent with adequate response time should
be chosen.
Selling Up Procedure
When designing a system using the SL4901491 transmitters and the M L920 series receivers, it is not necessary
to adjust the PPM rate on both transmitter and receiver.
The usual arrangement is to have a fixed resistor of 33 k
from pin 16 of the SL4901491 and to choose the capacitor
connected for pin 16 to pin 17 to give the required PPM
rate. The value is calculated from the formula to = 1.4CR.
Provided fairly close tolerance components are used for C1
and R1, then assembled transmitter units should be interchangeable without adjustment.
The timing components on the receiver can be selected
using the formula
1
40
f"
0.15CR wheref,,=-t;;
to being the PPM logic 0 time from the transmitter.
The value of R for the receiver should be between 47k
and 200 k, a typical arrangement being to use a 47 k fixed
resistor and a 100k pot as shown in Fig.6. The capacitor
should be selected from the above formula to give the
nominal frequency somewhere near the mid-range setting
of the potentiometer.
Final adjustment is made by setting the period on the
receiver oscillator time constant pin to 1140th of the transmitter PPM logic 0 time using the potentiometer.
Connection to the receiver time constant pin should be
made using a x 10 oscilloscope probe to reduce circuit
loading.
When adjusting the ML920, the monitor output can be
used for setting up, but in this case, a figure of 1120th of the
transmitter PPM logic 0 time should be used as the monitor
output is at half the oscillator frequency.
165
SL490
TO.
;~
ML020
SERIES
RECEIVER
osc.T/c
PIN
47k
).or
~-->-0.
100k
Fig.6 Recommended receiver time constant components
166
ABSOLUTE MAXIMUM RATINGS
Supply voltage
Total power dissipation
Operating temperature range
Storage temperature range
7V to 9.5V
SOOmW
_1O o e to +S5°e
-55°eto +125°e
CONSUMER
SL952
UHF AMPLIFIER
The SL952 amplifier has been designed to drive the
prescaler (SP4020, CT1110 etc) in a frequency
synthesis system directly from the tuners local oscillator.
It features a differential output to reduce local
oscillator radiation, and a differential input, which may
be used to couple the outputs from a VHF and a UHF
tuner (see Fig. 3).
The device operates from a single 5V supply with a
minimal number of external components and is encapsulated in a 14 lead DI L package.
[
,
[ 1
DiffERENTIAL OUTPUT
I~ :
GROUND
~
\4p '.Icc
13
PCONNECT TO
"
C"
on
[,
",
GROUND [ I
VtC
12p Vcc
} QIFfERENTIAllNPUT
Note: Ground all other unused pins
DP14
Fig. 1 Pin connections (top)
FEATURES
•
•
•
•
•
•
Low Cost
High Gain
Minimal External Component Count
Good Limiting Characteristics
1 GHz Respon3e
5V Supply
ABSOLUTE MAXIMUM RATINGS
Vce
+10V
Ambient temperature O°C to +65°C
Storage temperature -55°C to +125°C
Fig. 2 Test circuit
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated) :
Vee = 5.0V
TAMB = +25°C
Value
Characteristic
Supply voltage
Supply current
DC output level
Output offset
Maximum differential output swing
Differential voltage gain
Differential voltage gain
Differential voltage gain
Min.
Typ.
Max.
4.75
5.00
70
3.2
100
5.50
90
600
30
30
15
35
35
26
600
Units
Conditions
V
mA
V
mV
mVp-p
dB
dB
dB
950MHz
100MHz
500MHz
950MHz
167
SL952
TUNER
e)
sUHF
'--'10-----"'9
11
12
VHF
13
LO
.5V
Fig. 3 Typical application for TV frequency synthesis
168
CT
1110
4
•
CONSUMER
PLESSEY
Semiconductors
SL1430
TV IF PREAMPLI FI ER
The SL1430 is a fixed gain IF preamplifier for
television with an output optimised for driving Plessey
second generation low .capacitance surface acoustic
wave (SAW) filters. The addition of one external
capacitor allows the amplifier to drive normal capacitance SAW filters from Plessey or from other manufacturers.
The device features on chip decoupling and differerential output, requiring a minimal number of external
components to be used.
'"0'"
DIfFERENTIAL {
2
6
OUTPUT
1
1 GROUND
•
8
NC
Nt
INPUT
Fig. 1 Pin connections (top view)
FEATURES
•
•
•
•
•
•
Low cost
Low noise
Low external component count
Low distortion
Direct 12V operation
Can be used with different types of SAW
filters
, -_ _ _ _ _ _ _-<>
•
•
•
"
....---1---If---o
'.PUTT,
"
7·Sp
26dB gain at 40MHz
12V supply at 25mA
120mV rms. input handling
OUTPUT
"
'.L.---
80
---l
II:
l2
I
1\
~
60
I
\
-'
<
Z
~
·
4
Q
~
~
I
20
°E
I
i
I
;
20
II:
,.
l2-'
<
Z
----
-
r--l-------+
1--
20mV WANTED SIGNAL
---
"iii
~
!;;
\
1\
0
•
so
"C
I
!.
'g
E
~
I
~
--
~
~
z
I
::>
1\1 ,..I
40
60
I
,.
..
,.I
6.
8.
UNWANTED FREQUENCY (MHz)
80
Fig. 6
UNWANTED SIGNAL (mV rms)
ClOSS
modulation performance V frequency of unwanted
signal (see note 1)
Fig. 4 Cross modulation performance (see note 1)
".
i
..
~ ,
,
!.
I
>
.. 8.
I
'..".-
E
6. r-
~
z
"iii
--
f--
~
~
ffi
-r--
Z
-
::>
•o
i
,----
_~
i
~
I
60
I
i
!
20
r----+
I
Fig. 9 Intermodu/ation performance (see note 2)
I
I
i
o
°
20
30
SUPPLY VOLTAGE (V)
Fig. 8 Intermodulation performance v. supply voltage
NOTE 1.
Signal level refers to peak rms. i.e. The effective sync. tip level of a composite video signal.
NOTE 2.
The test signal employed corresponds to the red bar of a transmitted colour bar and consists of the following elements related to
the sync. tip level. the vision carrier at 38.9M Hz-6d8, the colour carrier at 34.5M Hz-18dB. and the SOtJnd carrier at 33.4MHz-7dB.
ABSOLUTE MAXIMUM RATINGS
Supply voltage
Operating temperature range
Storage temperature range
-O.5V to +25V
-10°C to +65°C
-55°C to + 125°C
171
172
CONSUMER
SL 1431/2
TV IF PREAMPLIFIERS WITH AGe GENERATOR
The SL1431 and SL1432 are fixed gain I F preamplifiers for television with a differential output optimised for driving Plessey surface acoustic wave
(SAW) filters. Besides providing the necessary gain
block between the tuner and SAW filter they also supply
a properly derived, broadband AGe signal to the tuner,
the SL1431 providing the correct SPrlse signal for a
PNP tuner, and the SL1432 for an NPN tuner. The
tuner AGe threshold is internally preset to a value to
allow adequate signal handling in the SL1431 and
SL1432 and does not normally require any external
adjustment. However, to account for the large variations in signal handling capability which is encountered
on some tuners, the tuner AGe threshold may be
externally adjusted by altering the bias on pin 1.
Both devices feature on-chip decoupling for a
minimum external component count.
AGCONSHADJLJSTO~
AGCDECOUPLtNG
2
1
AGe OUTPUT
OlffERENTlAL{
J
6
GROUND
OUTPUT
4
0
INPUT
Vee
DPS
Fig. 1 Pin connections
FEATURES
AGe Signal
For high input signal levels the voltage on pin 7 goes
low with SL1431 and high with the SL1432.
QUICK REFERENCE DATA
•
•
•
•
26dB Gain at40MHz
1 2V Supply at 25mA
120mV R.M.S. Input Handling
15mA Tuner AGC Capability
•
•
•
•
•
•
•
Properly Derived Tuner AGC
Low Cost
Low Noise
Low External Component Count
Low Distortion
Direct 12V Operation
Can be used with Different Types of SAW
Filters
, - - - - , . - - - - < > +Vcc
+--l
~~C~UPLE o - - - - + - - <
Fig. 2 Block diagram
1
---<:I
Vee
1+12VI
'.PUTT'"
'·5,
5
50
'~}OUT
L-~--l'~
"I
AGe
ONSET
ADJUST
Fig. 3 Test circuit
173
SL1431/SL1432
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Tamb = + 125°C
Supply voltage = + 12V
Frequency = 40MHz
Output load = 7.5pF (Pins 3 and 4)
Measurements made using test circuit Fig. 3.
Characteristic
Pin
Supply Voltage
Quiescent Current
Cut-off frequency (-3dB)
Voltage gain
Input signal for 46dB
intermodulation
Input signal for 1 % crossmodulation
Input signal for 1 dB sync tip
compression
Noise figure
Input impedance
Tuner AGC
Output current
Input impedance
2
2
5
Min.
Value
Typ.
7
15
60
23
12
25
110
26
Max.
13.5
33
29
Conditions
Units
V
mA
MHz
dB
Pins
olc
5
120
mV
Red colour bar
5
75
mV
(wanted level 20mV" unwanted,
modulation 65%)
5
5
5
130
7
1
15
mVrms
dB
4
3000
114.2pF
@ 10.0 V
mA
kO
20
6
Fig. 4 Typical applications
SL1431 TYPICAL CHARACTERISTICS AT .12V. +25°C. WITH SW173 AS LOAD (7.5pF)
(FIGS. 5 TO 10) Unwanted signal with 65% amplitude modulation at 10KHz
I
I
,
~ 100~--------+---~-----+----4---~
>
a:
§
mo ----
I
I
I
,
_._.
I
Fig. 6 Cross modulation performance V supply voltage
(see note 1)
SL1431/SL1432
,oor----,-------;--------~------,
c
c
a:
::
z"
'iii"
-'
10
------t-----+----+----J
:;
ffi
>-
~
!g
r
:;J
>-
a:
Z
~
I
::J
i
Z
',o~
::
i
____~------_:':_------..,,:':O-------..,J
ffi
a:a:
"z
(J
UNWANTED FREQUENCY (MHz)
0
Fig. 7 Cross modulation performance V frequency of unwanted
signal (see note 1)
iii
;;
60
V
=--!4+---1
I_-t------l
I
1 - - - - ----i---+--t----j
I
I
10
i
~
i
I
I
i
i
15
20
30
SUPPLY VOLTAGE (V)
Fig. 9 Intermodulation performance v. supply voltage
I
I
i
..........
~
~
i
I
K
I
I
I
20
°°
i
ADDITIONAL (TO SW173) CAPACITANCE (pFl
Fig. 8 Intermodulation performance v. load capacitance
VISION CARRIER (mV rms)
see note 2
Fig. 10 Intermodulation performance (see note 2)
NOTE 1.
Signal level refers to peak rms. i.e. The effective sync. tip level of a composite video signal.
NOTE 2. The test signal employed corresponds to the red bar of a transmitted colour bar and consists of the following elements related to
the sync. tip level. the vision carrier at 38.9M Hz-6dB. the colour carrier at 34.5MHz-18dB. and the sound carrier at 33.4M Hz-7dB.
ABSOLUTE MAXIMUM RATINGS
Supply voltage
Operating temperature range
Storage temperature range
-O.5V to +25V
-100 e to +65°e
-55°e to + 1 25°e
175
176
.~!e!
CONSUMER
SL 1440
PARALLEL SOUND AND VISION IF AMPLIFIERS AND DETECTORS
This Ie is designed to operate with a two output
port surface acoustic wave I F filter, one output for
vision and chrominance carriers with no sound carrier,
and one output for the sound carrier only.
The Ie amplifies and detects the sound and vision
carrier in two separate channels, the detectors being of
the wide band switching type. not requiring any tuning.
An AGe system is applied to the vision channel, the
sound channel being made to hard limit.
There is no facility for tuner AGe, an SL1431 should
be used to provide this signal. operating before the
SWAF to provide superior overload performance and
needing no preset adjustment.
VIO£OO/P'
-
ItO AliCTIMHONSTANT
Vet
2
13
SOUNDO/P
EARTH
3
12
EAfHH
mCOUPUNG
f '
VISIDNCAARIER {, :
"I
10
9
O[tOUi"LlNG
} SOUNOCAARlfRl/P
"-----'
DP14
Fig. 1 Pin connections (top view)
Fig. 2 Typical application SL1440
.I
I OV~~~~T
.1
VISION
INPUT
1
SOUND
INPUT
~--6-_ _ _ _---,1 ~
"
SOUND IF OUTPUT
Fig. 3
Ie block diagram.
177
178
CONSUMER
TV CIRCUITS
SP4020 SP4021
VHF/UHF -;- 64 PRESCALERS
The SP4020 and SP4021 are ECl divide by 64s
which will operate at frequencies in excess of 950MHz,
and are intended for use as prescalers in television
receiver synthesiser tuners.
The SP4020 has separate inputs for VHF and UHF
and the devices have a typical power dissipation of
470mW at the nominal supply voltage of +6.BV.
VHF INPUT (SP4C20 ONLY)
~.r---: ~l v"
2
13~
UHF INPUT
3
12P
ReFl
5
10
REF2
BAND CHANGE
INPUT
6
,
"
,
OUTPUT
Iv"
DG14
FEATURES
Fig. 1 Pin connections
•
Dual Input Ports for VHF and UHF
(SP4020)
Self-Biasing Clock Inputs
•
•
Variable Input Hysteresis Capability for
Wide Band Operation
•
TTL/MOS Compatible Band Change Input
(SP4020)
II Push-Pull TTL O/P
OPERATING NOTES
Two input ports are available on the SP4020.
Switching between these inputs is accomplished by
operation of the band change input. A logic '1'
activates the UHF input. logic '0' the VHF input. When
an input is not in use the input signal must be removed
to prevent cross-modulation occuring at high frequencies. Both inputs are terminated by a nominal
4000 and should be AC coupled to their respective
signal sources. Input power to the device is terminated
to ground by the two decoupling capacitors on the
reference pins. Input coupling and reference decoupling
capacitors should be of a type suitable for use at a
frequency of 1 G Hz.
When the device is switched to the VHF input. an
input hysteresis of 50mV is set by the internal band
change circuit. This improves the low frequency sinewave operation of the device. The hysteresis level may be
measured as VREF 1 -VREF 2
If the SP4021 is required to operate with a sinewave
input below 100M Hz, then the required hysteresis
may be applied externally as shown in Fig. 5. large
values of hysteresis should be avoided as this will
degrade the input sensitivity of the device at the maximum frequency. The divide by 64 output is designed to
interface with TIL which has a common VEE (ground).
At low frequency the output will change when one
of the clock change inputs changes from a low to a high
level. Self oscillation may result if the input signal falls
below the minimum specified.
The devices may be operated down to very low
frequencies if a square wave input with an edge speed
greater than 200V / ~s is used.
Fig.2
Equivalent small signal input impedance (80MHz-IGHz)
SAMPLING SCOPE
t
50A liP
=
VHF INPUT
SP4020 ONLY
SAMPliNG
SCOPE
SOnljP
6·611
~O
3SV
Only one generator should be connected to either the
VH F or UHF inputs. The input not in use may be left open
circuit. All capacitors are 1 nF unless otherwise stated.
Fig. 3
AC test circuit
179
SP4020 ISP4021
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Supply voltage VEE = oV. Vee = +6.45V to + 7.15V
Clock input voltage sinusoidal
TA: +25'C
Pin 14 OIP
Characteristic
Value
Pin
Supply voltage
Supply current
Output level high
Output level low
Band change input (SP4020 only)
High level
Low level
Low level liP current
Max. clamp current
Sensitivity
SP4020 :VHF liP 100MHz
VHF liP 300MHz
UHF liP 500-800MHz
UHF liP 950MHz
SP4021 :liP 100MHz
liP 300-800MHz
liP 950MHz
Overload level
SP4020 :VHF liP 100-300MHz
UHF liP 100-950MHz
SP4021 :liP 100-300M Hz
liP 500-950M Hz
1.2
1.2
4
4
14
14
14
14
Units
Min.
Typ.
Max.
6.45
40
2.5
6.80
68
3.5
0.3
7.15
90
5.0
0.5
V
mA
V
V
0.4
-0.8
V
V
mA
mA
2.5
-3
8
10
10
Conditions
Vee = 6.8V
-1mA
5mA
See Note 1
For UHF input
For VHF input
@O.4V
@ -0.7V
100
50
100
50
300
300
300
300
mVp-p
mVp-p
mVp-p
mVp-p
See Note 2
120
100
50
400
300
300
mVp-p
mVp-p
mVp-p
See Note 2
8
10
0.9
0.9
2.0
2.0
Vp-p
Vp-p
10
10
1.0
0.9
2.0
2.0
Vp-p
Vp-p
Pin 14 to OV
Pin 14 to OV
Pin 14 to OV
Note 1 TTL type including negative input voltage clamp
Note 2 This is measured with the device in a low profile socket; soldered results show, typically, a 25% improvement.
CONTROL
FROM MOS
DEVICE
Connections to these pins should be made to have the
minimum series inductance. Capacitors should be of a
type suitable for use at 1 GHz.
Fig. 4 Application circuit
180
S P4020/S P4021
1000
1
900
BOO
Ii:
,
a.
>
50~
!
'11;
TTl OUTPUT
~
r---
I-600
I--
AREA OF
700
500
r---
400
I--
1
OPERATION
VHF INPUT
PIN 8
-
OF OPERATION
UHF INPUT
PIN 10
I
200
I
I
I
1
1
1
600
700
800
I 1 1
300
400
rrIl-
r-
I-J100
1
GUARANTEED AREA
-
I
'00
1
-
GUARANTEED
sao
1
1/
950
FREQUENCV (MHz)
Fig. 6 SP4020 typical sensitivity with limits of operation
when used in application circuit (Fig. 4)
Capacitors are 1 nF uniessl otherwise stated. Values
should be increased if operation below 10MHz is
required.
For 50mV hysteresis R1 = 36k QR2 = 00
For 100mV hysteresis R1 = 18k QR2 = 18k Q
1000
rra:, r~ 60 or.§ 50 or~ 40 orr-.; 30 0
...
0
~
900
GUARANTEED AREA
700
Fig. 5
Wideband operation
ABSOLUTE MAXIMUM RATINGS
Power supply voltage Vee - VEE
OV to +10V
Input voltage, clock inputs
2.5V p-p
Band change input
(SP4020)
+7.2 to -O.5Vor -lOrnA
Output current
+30mA to -30mA
Operating temperature
O°C to +65°C
Storage temperature
-55°C to +125°C
0
I..........
'00
200
l I
I
OF OPERATION
INPUT
PIN 10
I
I
I
1 J
1
1
1
JOO
400
1
I
I
1
1
1
6 0
I
700
I
J
J
1
00
FREQUENCY (MHz)
Fig. 7
SP4021 Typical sensitivity with limits of operation
when used in application circuit (Fig. 4) with pin
14 open circuit.
181
182
CONSUMER
lVCIRCUns
SP4040 SP4041
VH FlU H F -:- 256 PRESCAlERS
The SP4040 and SP4041 are ECl divide by 256
which will operate at frequencies in excess of 950MHz,
and are intended for use as prescalers in television
receiver synthesiser tuners.
The SP4040 has separate inputs for VHF and UHF
and the devices have a typical pOW<;lr dissipation of
500mW at the nominal supply voltage of +6.BV.
VHF INPUT (SP4040 ONLY)
,
UHF INPUT
3
REF 1
5
REF 2
6
~ " Iv..
"
"
!I
9
OUTPUT
I
BAND CHANGE 7
INPUT
"l-_ _
--r
Vel;
FEATURES
•
•
•
•
•
Fig. 1 Pin connections
Dual Input Ports for VHF and UHF
(SP4040)
Self-Biasing Clock Inputs
Variable Input Hysteresis Capability for
Wide Band Operation
TTL/MOS Compatible Band Change Input
(SP4040)
Push-Pull TTL O/P
PIN 1 0 0 - - - - , - - - ,
400
20
'oH
OPERATING NOTES
Two input ports are available on the SP4040.
Switching between these inputs is accomplished by
operation of the band change input. A logic '1'
activates the UHF input, logic '0' the VHF input. When
an input is not in use the input signal must be removed
to prevent cross-modulation occuring at high frequencies. Both inputs are terminated by a nominal
400 Q and should be AC coupled to their respective
signal sources. Input power to the device is terminated
to ground by the two decoupling capacitors on the
reference pins. Input coupling and reference decoupling
capacitors should be of a type suitable for use at a
frequency of 1 G Hz.
When the device is switched to the VHF input, an
input hysteresis of 50mV is set by the internal band
change circuit. This improves the low frequency sinewave operation of the device. The hysteresis level may be
measured as VREF 1 -VREF 2
If the SP4041 is requi red to operate with a sinewave
input below 100M Hz, then the required hysteresis
may be applied externally as shown in Fig. 5. large
values of hysteresis should be avoided as this will
degrade the input sensitivity of the device at the maximum frequency. The divide by 64 output is designed to
interface with TIL which has a common VEE (ground).
At low frequency the output will change when one
of the clock change inputs changes from a low to a high
level. Self oscillation may result if the input signal falls
below the minimum specified.
The devices may be operated down to very low
frequencies if a square wave input with an edge speed
greater than 200V I ~s is used.
PIN 6 . 7 o - - - - - - J
Fig.2
Equivalent small signal input impedance (80MHz-IGHz)
ZAMPLING SCOPE
SOro. lIP
t
=
VHF INPUT
SP4020 ONLY
SAMPLING
SCOPE
50.nI/P
6·aV!O 3SV
Only one generator should be connected to either the
VHF or UHF inputs. The input not in use may be left open
circuit. All capacitors are 1 nF unless otherwise stated.
Fig. 3
AC test circuit
183
SP4040/SP4041
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Supply voltage VEE = oV, Vee = +6.45V to + 7.15V
Clock input voltage sinusoidal
TA: +25°C
Pin 14 DIP
Characteristic
Supply voltage
Supply current
Output level:
High
Low
Band change input
High level
Low level
Low level lIP current
Max. clamp current
Sensitivity
SP4040 :VHF lIP 100MHz
300M Hz
UHF lIP 500-800MHz
950MHz
SP4041 :100MHz
200MHz
300MHz
500-700MHz
800M Hz
950MHz
Overload level
SP4040 :VHF liP 100-300MHz
UHF lIP 500-600MHz
SP1041 :100MHz
300MHz
500-600MHz
950MHz
Pin
Value
Units
Conditions
Min.
Typ.
Max.
1,2
1,2
6.45
50
6.80
70
7.15
95
V
mA
Vee = 7.15V
4
4
2.5
3.5
0.3
5.0
0.5
V
V
-1mA
5mA
14
14
14
14
2.5
0.4
-0.8
V
V
mA
mA
For UHF input}
For VHF input SP4040
0' O.4V
only
@ -O.7V
Pin 14 to OV
Pin 14 to OV
-3
10
10
120
100
100
250
300
300
300
440
mVp-p
mVp-p
mVp-p
mVp-p
10
10
10
10
10
10
400
300
150
100
200
400
550
400
350
300
400
700
mVp-p
mVp-p
mVp-p
mVp-p
mVp-p
mVp-p
Note 1
Pin 14 to OV
8
8
10
1.0
1.0
2.0
2.0
Vp-p
Vp-p
10
10
10
10
1.2
1.0
1.0
1.2
2.0
2.0
2.0
2.5
Vp-p
Vp-p
Vp-p
Vp-p
Note 1
Note 1. This is measured with the device in a low profile socket; soldered in results show typically a 25% improvement.
CONTROL
FROM MOS
DEVICE
Connections to these pins should be made to have the
minimum series inductance. Capacitors should be of a
type suilable for use all GHz.
Fig. 4 Application circuit
184
SP4040/SP4041
0200
~
GUARANTEEO AREA
OF OPERATION
GUARA.NTEED
"'1;
SOA
AREA OF
OPERATION
,
Q
TTL OUTPUT
>
!
r---
....
~
;:;
UHF INPUT
PIN 10
VHF INPUT
PIN 8
Q
-
'00
......
.6·6V
'00
'00
300
--
500
/'
I I
I I
I I
..v-
600
600
100
I
I
osO
FREQUENtV (MHz)
Capacitors are 1 nF unless otherwise stated. Value's
should be increased if operation below 10MHz is
Fig. 6 SP4040 typical sensitivity with limits af operation
when used in application circuit (Fig. 4)
required.
For 50mV hysteresis R1 = 36k OR2.= 00
For 100mV hysteresis R1 = 18k OR2 = 18k 0
Fig. 5
Wideband operation
,
Ii
100
0.. 600
>
ABSOLUTE MAXIMUM RATINGS
Power supply voltage Vee - VEE
OV to +10V
Input voltage, clock inputs
2.5V p--p
Band change input
(SP4040)
+7.2 to -O.5V or -10mA
Output current
+30mA to -30mA
Operating temperature
O°C to +65°C
Storage temperature
-55°C to +125°C
.§.
500
....
~
FREQUENCY (MHz)
Fig. 7
SP4041 Typical sensitivity with limits of operation
when used in application circuit (Fig. 4) with pin
14 open circuit.
185
186
•
PLESSEY
Semiconductors
CONSUMER
TV FILTERS
SW150 SW153 SW170 SW173 SW200
SW250 SW400 SW450
SURFACE ACOUSTIC WAVE COLOUR TV IF FILTERS
This comprehensive range of TV IF filters utilises
Plessey Surface Acoustic Wave technology and is
suitable for use in colour or monochrome television
receivers world wide. The frequency pass-band and
phase response of each of these highly stable devices
are tailored to the relative transmission standard. The
devices require no adjustment and are packaged in a
totally hermetic Metal/Glass T08 package.
BALANCED INPUT PINS 2&4
BALANCED OUTPUT PINS 1&5
CM5
CAN (SCREEN) PIN3
Fig. 1 Pin connections (viewed from beneath I
FEATURES
•
No Adjustment Necessary
•
•
•
•
•
Low Cost
Compact Dimensions
High Stability
High Reliability
Comprehensive Range of Standards
Available
.12V
Fig. 2 Typical application
APPLICATION NOTES
The input drive and output load circuitry should
provide a low impedance across at least one device port
to minimise spurious signals due to secondary device
characteristics. Fig. 2 shows a typical application,
the SL1430 providing a very low drive impedance. The
330 n load resistor is included to ensure stability of
the TDA2540 and may be omitted in some designs that
do not use this device.
Care must be taken with the printed circuit board
layout, and the use of balanced input and output is
advised to ensure low levels of direct breakthrough.
The device must also be mounted with minimum lead
length. Application introduced direct breakthrough will
exhibit itself as a deterioration in amplitude and group
delay ripple, and a screen image approximately 1.5fts
before the main response.
SAWF
100
INPUT
-@l } ~~~:~~ED
nh TO 50.n
-r_C::r__-@MEASURING
EQUIPMENT
v-
'"'
Fig. 3 Test circuit
187
SVV150/153/170/173/200/250/400/450
-t;;;2~;;::2~~
.~.
IN-BAND LEVEL
~ _we
IN-BAND LEVEL
-t7<---,
0 ••
6'.
-6dB
IN BAND
LIMITS
--;
y-UPPER sIDe
LOWER SlOE l e i
REGION
LOi
ADJACENT SOUND TRAP
ADJACENT VISION TRAP
FREQUENCY
Fig. 4 Amplitude characteristics
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated) :Ambient temperature
+35 D C
Input drive impedance
500
Load impedance
3000 balanced
The amplitude level at the vision carrier frequency is
taken to be -6dB and is then used as a reference for all
other relevant measurements (see Fig. 4).
The insertion loss is defined as the voltage ratio
V1NJVOUT in the test circuit (Fig. 3) and is expressed in
dB.
The amplitude characteristics given in the Electrical
Characteristic tables are defined in Fig. 4. The response
in the Nyquist region is guaranteed by the measurement of the 2T sin' pulse and bar K rating after
synchronous demodulation.
In band amplitude and group delay ripple is defined
as the worst deviation from the mean over any 500Khz
bandwidth between the two defined in-band frequency
limits.
The measurement of spurious outputs includes those
due to internal reflections and direct breakthrough, a
2T Sin' pulse being used and measurements being made
between 2 and 1 fls before, and 1 and 4fls after, the
centre of the main response.
SW150
The SW150 is a TV IF filter for the United Kingdom PAL standard, system I, with a vision carrier frequency of 39.5MHz.
Characteristic
Vision carrier
Colour carrier
Sound carrier
Sound shelf deviation
In-band level
In band spot
In-band slope
In-band ripple
Adjacent vision trap
Adjacent sound trap
Lower side lobe
Upper side lobe
Insertion loss
2T sin' pulse and bar K rating
Group delay:Ripple
Deviation
Spurious outputs
Temperature coefficient of frequency
Small signal impedances
Input pins 2 & 4
Output pins 1 & 5
188
Frequency
MHz
39.5
35.1
33.5
33.2-33.8
36-38
38
35.5
36-38
31.5
41.5
26.5-31.5
41.5-46.5
46.5-100
38.0
39.5
Value
Min.
Typ.
Max.
Ref. level -6
-7
-3
0
-27 -24
-21
±3
-3
0
2
-2
0
1.5
0
-2
-4
0.5
1
-45 -55
-42 -50
-38 -45
-36 -42
-30
17
21
1.5
2
36.0-39
34.5-40.5
5
10
10
40
39.5
-46
-90
-40
1kO/l
12pF
1.6kO//
10pF
Units
dB
dB
IdB:
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
%
ns
ns
dB
ppm/DC
Conditions
w.r.t. level at 38MHz
Peak
SVV150/153/170/173/200/250/400/450
SW153
The SW153 is a TV IF filter for the United Kingdom PAL standard, system I, with a vision carrier frequency of
39,5MHz,
Character;stic
Frequency
MHz
Vision carrier
Colour carrier
Sound carrier
Sound shelf deviation
In-band level
In band spot
In-band slope
In-band ripple
Adjacent vision trap
Adjacent sound trap
Lower side lobe
Upper side lobe
Insertion loss
2T sin' pulse and bar K rating
Group delay:Ripple
Deviation
Spurious outputs
Temperature coefficient of frequency
Small signal impedances
Input pins 2 & 4
39,5
35,1
33.5
33.2-33,8
36-38
38
35.5
36-38
31.5
41,5
26,5-31.5
41,5-46,5
46.5-100
38.0
39.5
Value
Min,
Typ.
Max.
R~f,
level -'-6
-3
0
-19
-22
:t 1
=3
-2
0
2
1,5
-1,5 0
-1
-2
0
0.5
1
-45 -55
-40 -50
-40 -50
-36 -42
-30
21
25
1.5
2
-6
-25
36.0-39,0
34,5-40,5
5
10
10
40
39,5
-46
-90
-40
Units
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
Conditions
w,r.t. level at 38MHz
Peak
%
ns
ns
dB
ppm/oC
1.6k all
8pF
1.8kO!!
10pF
Output pins 1 & 5
SW170
The SW170 is a TV IF filter for the European PAL standard, systems Band G, with a vision carrier frequency of
38,9MHz,
Characteristic
Frequency
MHz
Vision carrier
Colour carrier
Sound carrier
Sound shelf deviation
In-band level
In band spot
In-band slope
In-band ripple
Adjacent vision trap
VHF
UHF
Adjacent sound trap
UHF
VHF
Lower side lobe
Upper side lobe
Insertion loss
2T sin' pulse and bar K rating
Group delay:Ripple
Deviation
Spurious outputs
Temperature coefficient of frequency
Small signal impedances
Input pins 2 & 4
Output pins 1 & 5
Value
Min.
Typ.
Units
38,9
34,5
33.4
33,1-33,5
35,5-37,4
37.4
35,5
35,5-37.4
Ref, level -6
-7,5
-4
-2.5,
-27
-22
-18
:',3
0
2
-3
1,5
-1.5 0
-2
-3
-0,5
0.5
1
dB
dB
dB
dB
dB
dB
dB
dB
30,9
31,9
-36
-38
-40
-45
dB
dB
40,4
41.4
27.5-31,9
40.4-45
45-100
37.4
38,9
-38
-36
-35
-35
-45
-40
-40
-40
-20
18
2
dB
dB
dB
dB
dB
dB
%
36-38
34,5
35.15
36,9
25
170
0
-90
38,9
-46
-90
Conditions
Max.
24
3
ns
ns
ns
ns
-40
w,r,t. level at 37.4MHz
Peak
Peak
Reference 0 @ 38,9MHz
Reference 0 @ 38.9MHz
Reference 0 @ 38,9MHz
dB
ppm/oC
1kO//
12pF
1,6kO!!
10PF
189
SVV150/153/170/173/200/250/400/450
SW173
The SW173 is a TV IF filter for the European PAL standard, systems Band G, with a vision frequency of 38.9
Characteristic
Frequency
MHz
Value
Min,
Typ.
Units
Vision carrier
Colour carrier
Sound carrier
Sound shelf deviation
In-band level
In-band spot
In-band slope
In-band ripple
Adjacent vision trap
VHF
UHF
38.9
34.5
33.4
33.1-33.5
35.5-37.4
37.4
35.5
35.5-37.4
Ref. level -6
-5
-3.5
-2
-23 -20
-17
+4/-1 +6/-3
0
1
-2
-1
1
0
-1.5
-2.5
0
0.75
1.5
dB
dB
dB
dB
dB
dB
dB
dB
30.9
31.9
-40
-43
-43
-48
dB
dB
Adjacent sound trap
UHF
VHF
40.4
41.4
-43
-40
-48
-43
dB
dB
27.5-3 •. 9
40.4-45
45-100
37.4
38.9
-36
-37
-40
-42
-30
22
2
dB
dB
dB
dB
Lower side lobe
Upper side lobe
Insertion loss
2T sin' pulse and bar K rating
Group delay
Ripple
Deviation
Spurious outputs
Temperature coefficient of frequency
Small signal impedances
Input pins 2 & 4
Conditions
Max.
26
3
36-38
34.1
34.5
35.15
36.9
37.9
39.9
25
400
170
0
-90
-53
-53
50
38.9
-46
-90
-40
wrt level at 37.4MHz
Peak
%
ns
ns
ns
ns
ns
ns
ns
Peak
Reference
Reference
Reference
Reference
Reference
Reference
0
0
0
0
0
0
@ 38.9M Hz
Cal 38.9M Hz
Cal 38.9MHz
(al38.9MHz
Cal 38.9MHz
@ 38.9M Hz
dB
ppm/DC
1.6kO//
8pF
1.8kO//
10pF
Output pins 1 & 5
SW200
The SW200 is a TV IF filter for the North American NTSC standard, systems M and N, with a vision carrier frequency
of 45.75MHz.
Characteristics
Frequency
MHz
Typ.
Vision carrier
Colour carrier
Sound carrier
In-band level
In-band ripple
Adjacent vision trap
Adjacent sound trap
Lower side lobe
Upper side lobe
Insertion loss
2T sin2 pulse and bar K rating
Group delay:Ripple
Deviation
45.75
42.17
41.25
43-44.25
43-44.25
39.75
47.5
35-39.75
47.5-52.5
43-44.25
42-46
10
50
Spurious outputs
Temperature coefficient of frequency
Small signal impedances
Input pins 2 & 4
45.75
-44
-90
Output pins 1 & 5
190
Value
Min.
Units
Ref. level -6
-7
-4
0
-24
-20
-16
-3
0
3
0.5
1.5
-40
-50
-35
-45
-35
-40
-30
-36
25
19
2
3
1kO//
13pF
1.5kO//
11 pF
Conditions
Max.
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
%
ns
ns
-38
dB
ppm/DC
Peak
SVV150/153/170/173/200/250/400/450
SW250
The SW250 is a TV IF filter for the French SECAM standard, systems Land L' , with a vision carrier frequency of
327MHz
Characteristic
Frequency
MHz
Vision carrier
Colour carrier region
In-band level
In· band ripple
Adjacent vision trap
Adjacent sound trap
Own sound
UHF
VHF
Lower side lobe
Upper side lobe
Insertion loss
2T sin' pulse and bar K rating
Group delay:Ripple
Deviation
Spurious outputs
Temperature coefficient of frequency
Small signal impedance
Input pins 2 & 4
Value
Min.
Units
Typ.
32.7
37
38
34.5-36
34.5-36
40.7
31.2
Ref. level -6
0
1
-9
-6
0
2
0.5
1
-38 -43
-46 -50
dB
dB
dB
dB
dB
dB
dB
39.2
43.85
-43
-43
-46
-46
dB
dB
26-31.2
39.2-40.7
40.7-45
45-90
34.5
32.7
-36
-38
-36
-40
-43
-40
-30
19
2
dB
dB
dB
dB
dB
-2
-3
-2
34.5-36
34.5-36
10
10
32.7
-46
-90
Conditions
Max.
25
3
Peak
%
ns
ns
50
-40
dB
ppm/DC
1.6k all
10pF
1.2k n//
11 pF
Output pins 1 & 5
SW400
The SW400 is a TV IF filter for the Australian PAL standard, systems Band G, with a vision carrier frequency of
36.875MHz.
Characteristic
Frequency
MHz
Vision carrier
Colour carrier
Sound carrier
In-band level
In band ripple
36.875
32.445
31.375
33.47535.375
33.47535.375
Value
Min.
Typ.
Units
Ref. level -6
-7
-3
-1
-26 -22
-18
dB
dB
dB
-3
2
dB
1.5
dB
0
0.5
Adjacent vision trap
VHF
UHF
28.875
29.875
-36
-38
-40
-45
dB
dB
Adjacent sound trap
VHF
UHF
28.375
39.375
-38
-36
-45
-40
dB
dB
-35
-40
dB
-35
-40
18
2
Lower side lobe
Upper side lobe
Insertion loss
2T sin' pulse and bar K rating
Group delay
Ripple
Deviation
Spurious outputs
Temperature ·coefficient of frequency
Small signal impedances
Input pins 2 & 4
Output pins 1 & 5
25.029.875
38.37543.0
35.375
36.875
32.5-35.375
32.445
34.125
34.875
25
175
0
-80
36.875
-46
-90
Conditions
Max.
24
3
dB
dB
%
ns
ns
ns
ns
-40
Peak
Reference 0 (it 36.875MHz
dB
ppm/DC
1 kO//
12pF
1.6k all
10pF
191
SVV150/153/170/173/200/250/400/450
SW450
The SW450 is a TV IF filler forthe South African PAL standard. system I. with a vision carrier frequency of 38.9MHz.
Frequency
Characteristic
MHz
Value
Min.
Typ.
Vision carrier
Colour carrier
Sound carrier
In-band level
In-band ripple
Adjacent vision trap
Adjacent sound trap
Lower side lobe
Upper side lobe
Insertion loss
2T sin' pulse and bar K rating
Group delay:Ripple
Deviation
38.9
34.47
32.9
35.5-37.4
35.5-37.4
30.9
40.9
25.8-30.9
40.9-46
37.4
38.9
35.5-37.4
35.5-37.4
10
25
Spurious outputs
Temperature coefficient of frequency
Small signal impedances
Input pins 2 & 4
38.9
-46
-90
Output pins 1 & 5
ABSOLUTE MAXIMUM RATINGS
Storage temperature
Operating. temperature
Pin to pin voltage
Pin to case voltage
192
_25°C to +85°C
-10°C to +70°C
30V (short term)
10V (continuous)
100V
Units
Ref. level -6
-7
-4
0
-34
-30
-26
-3
0
2
0.5
1.5
-38
-46
-38
-43
-36
-40
-40
-36
17
23
1.5
2
1 k011
12pF
1.6kOII
10pF
Conditions
Max.
50
-40
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
%
ns
ns
dB
ppm/DC
Peak
5VV150/153/170/173/200/250/400/450
TYPICAL AMPLITUDE RESPONSES
o
-10
-20
""o -30
....J
-40
SW 150
-50
-60
26
8
28
30
32
Plessey
34
36
38
Frequency (MHz)
40
42
44
46
-10
-20
""o
-30
....J
-40
-50
__L--L~~L--L~__L--L~__L--L~--....l
34
36
38
40
42
44
46
Frequency (MHz)
_60L-....l-~L-~~~~L-....l-~
26
e
28
Plessey
30
32
193
SVV150/153/170/173/200/250/400/450
o
-10
II
II
o
-30
oJ
-40
-50
e
28
e
28
30
32
34
36
38
Frequency (MHz)
40
42
44
32
34
36
38
·Frequency (MHz)
40
42
44
Plessey
-10
II
II
o
-30
oJ
-40
-50
194
30
Plessey
SVV150/153/170/173/200/250/400/4&O
-10
-20
(,l
(,l
o
-30
.J
-40
-50
36
S
40
38
42
44
46
48
50
52
Frequency (MHz)
Plessey
-10
(,l
(,l
o
-30
.J
-40
-50
26
S
C?8
Plessey
30
32
34
36
38
40
42
44
Frequency (MHz)
195
SVV150/153/170/173/200/250/400/450
-10
-20
""o -30
...J
-40
-50
-60
~-'---'-----,-----,------"~~-----"------,--....L.:..:..:..~~---'-26
8
28
32
30
34
Frequency
Plessey
36
40
38
42
(MHz)
-10
-20
"
o" -30
...J
-40
-50
26
8
196
28
Pl essey
30
32
36
38
Frequency
34
(MHz)
40
42
44
46
CONSUMER
lVCIRCUITS
TBA120S
UMmNG IF AMPUFIERlFM DETECTOR
The TBA 1205 is a symmetrical a·stage limiting amplifier
with a symmetrical coincidence demodulator and remote
DC volume control. The circuit is especially suited for the
sound I F section of TV receivers and for FMII F
amplification/demodulation in FM radio receivers.
An auxiliary circuit, consisting of a transistor with free
base and collector and a 12V Zener diode, is also
incorporated on the chip. The transistor can be used as an
AF preamplifier (lc<5mA) or as a bass/treble switch using
voltage·controlled on/off switching of an R·C circuit.
The Zener diode can be used to stabilize the chip supply
voltage or that of other circuits in the system (lz<15mAl.
The TBA 1205 is supplied in two group variants, with
volume as the parameter. A decrease in volume of 30 dB
requires a resistor between pin 5 and earth with a value
depending on the group number as shown in the following
table. The group number is printed on the package.
EARTH[~PINPUT
lIP BIAS[
l
II
FREE COLLECTOR [
I
'I
FREE BASE [
4
H
VOLUME CONTROL [
5
fa
LIM. AMP OIP I [ •
TUNED CC1[
7
I
•
PF:::eOBACK BIAS
PZENER DIP
P+ 'Ie
p
SUPPLY
LIM. AMP O/P2
P
P
TUNED eeT
AUDIO O/P
DP14 OP14
F;g. 1 Pin connections
FEATURES
Group
III
IV
RS(km
2.1-2.S
2.4-2.9
III
III
II
II
Outstanding Limiting Qualities
High AM Suppression
Wide Supply Voltage Range
Low External Component Count
APPLICATIONS
IiII
III
II
1------
TV Sound Systems
FM Rad io Receivers
FM Tuners
I
I
I
QUICK REFERENCE DATA
_____1
,,~
A"P
OIPI
III
I?I
III
III
II
II
I!I
Supply VOltage\: + 12V (Typ)
Operating Frequency: Up to 12MHz
Current Consumption: 14mA (Typ.)
I F Voltage Gain: 68dB (Typ.)
AF Output Voltage: 1.1 V r.m.s. (Typ.)
Volume Control Range: 70dB (Typ.)
Second Source Availability
Fig. 2 SBA 120S block diagr8m
197
TBA120S
ELECTRICAL CHARACTERISTICS
Test Condition. (unle.. otherwise stated):
Vee = +12V
TA =+25°C
f= 5.5MHz
~f = ±50kHz
f mod = 1kHz
Value
Characteristics
Symbol
Units
Min.
Typ.
Conditions
Max.
Amplifier/demodulator
Frequency range
IF voltage gain V6N 14
IF output voltage
AF output voltage
f
Vopp
VAF
Input voltage at start of limiting
Input impedance
Output resistance (pin 8)
Volume control range
Vlim
Zj
Ro
VAF max
VAF mjn
Va
aAM
R5
DC component of olp signal
AM suppression
Potentionmeter resistance
-ldB down
-7OdBdown
Control voltage
-ldB down
-70dB down
Total current requirement
12
0
Gv
15/6
68
250
1.1
0.55
30
40/4.5
2.6
70
60
MHz
dB
mV
V r.m.s.
V r.m.S.
p.V
kU/pF
kU
dB
45
7.3
55
V
dB
3.7
1.4
4.7
1.0
kU
kU
2.6
Icc
10
12
2.4
1.3
14
16
V
V
mA
mA
V12
Rz
BVeEo
hFE
12.5
13.5
30
14.5
Limiting each output
Vj=10mV, 0=45, K=4%
Vj=10mV, 0=20, K=l%
0=45
Vj=O
Vj=500p.V, m=30%
V5
18
20
R5 = 00
Rs = 0
Auxiliary circuit
Zener voltage
Zener resistance
Transistor breakdown voltage
Current gain
ABSOLUTE MAXIMUM RATINGS
u,
Supply voltage Vee:
Operating temperature
Storage temperature
Total power dissipation, Ptot
Continous:
Max. 1 min:
198
18V
_10°C to +70°C
_25°C to +125°C
400mW
500mW
13
30
V
U
V
-
Zener current, 112
Continuous:
Max. 1 min:
Volume control voltage, Vs:
Collector current, 13:
Current 14:
Shunt resistance R13/14:
112 = 5mA
14=O,13=500p.A
13=lmA
15mA
20mA
4V
5mA
2mA
..;; lkU
TBA120S
0
°
V
0
I
-2
°
-)
°
,f-
~::>
'.
",
-+-T12 V
•
" -, °
5·5~Hz
II
V
/
"
10m'"
"
-
J
1/
"
I
f--
1_
60
I- - l - t-
V-.
10
II
t-- ----
r-r- t'-.
- 8o,,O-L......L.··
10
/
SOkHz
I :
• 5'Slo4Hz
I
10
6.f:
• 50kHz
o::>
I
: tOmv
1/
J
o
::>
V
I
0
I
II
§
' !'" I
20
vee ~
-S 0
o
I-
/
°
/"
/1
..
6
I
PINS ole
-
.Sf-- -_
Fig. 4 Volume control resistance characteristic
'"
t"
1-
k=I.!i'/. C =InF/2.2.k1l.
1"'-
1t:)"oC }680pL.kAI
I"-
I
"
~
20
50
-4 0
~
20
AUDIO OUTPUJ LEVEL VAF RElATIvE
TO MAl(, O/PldB!
VOLTAGE "eeIV!
"
Fig. 5 Audio output v. supply voltage
Fig.·6 Distortion factor (k) as a function of audio output voltage
VAF
199
TBA120S
"
Ii
I
,
r---....
"
/
,
.
.
v
1/
,
I-
/'
V
v
l'-
/
I
V
,
,
10"2
.'
,,'
INPUT
,,'
VOLTAGE Vj
,,'
,,'
(mY I
Fig. 7 AM suppression characteristics
Frequency
(MHz)
Fig. 8 Recommended application circuit, 5.5MHz
Fig. 9 Application circuit using ceramic filter. (For good
selectivity. the ceramic filter should be combined with an LC
S.O
5.5
4.5
[>
circuit)
:~
,,~
Fig. 10 Circuit diagram
200
Filler
(Murale Type No)
SFES.OMB
SFE5.5MB
SFE4.5MB
R(m
470
680
1k
CONSUMER
1V CIRCUITS
TBA120T TBA120U
FM IF AMPUFIER AND DEMODULATOR
The TBA120T and TBA120U are symmetrical 8·stage
limiting
amplifiers
with
symmetrical
coincidence
demodulator and remote DC volume control. The circuits
are especially suitable for the sound IF section of TV
receivers and for FM/IF amplification/demodulation in FM
radio receivers. An additional audio output is provided at
constant level (before the volume control) for the
connection of video recorders and headphones, together
with an audio input for video recorder playback.
The audio output voltage is at constant level with supply
voltages between 10 and 18V and is of the same level as the
TBA 120S operating from a 15V supply.
The devices are insensitive to supply voltage hum, and
there is therefore little need for smoothing capacitors.
FEATURES
•
II
II
II
II
II
II
Outstanding Limiting Qualitites
High AM Suppression
Wide Supply Voltage Range
Low External Component Count
Low Intermodulation due to I F Voltage
No
Selection
for
Volume
Control
Characteristic Necessary
Designed for use with Ceramic Filters
(TSA 120T only)
IF IiPnOWL
"
HfF. VOLIAGlO/P
t TBA120u II
VOLUME C0
4' .
."/
.>0
-70
·20
V t--
·lO
i--
t--
~
.6~[ -SO
."
." ~OO::p"
.90/,
- : : V,_
V
~
m.1I0'!,
f- t---
\
.
;tOlSj
t--.:
'mod' 1kHz -
.,,,,
iii
(T8A 720U onlyl
Fig. 1 AF output voltage and noise voltage v. input voltage (input
f--
tOdj'hffl
Oel8.770mV,n
-~o
\
·30
-20
,\1
I.
-10
9
:r WIT~
I. !25kHI. II.'"
AM· SUPPRESSION
dB
I'\.
"
I
~O'r. f- I 1
m. ,' ' ' '
NOISE
"-L
30llV
v,
1
m.
1
\ II
l
~
200m'... AT ''" , , OEEMPHlslS
,~
I'..
·00
301''1
m.O
1I"!5DltHl . . . 3'J. WITH DEEMTASIS
Ij
1\
\
~
Murata SFE 5.5MB!
1/
·lO
11
I
-60 I'~
V·70
V
·lO
"U"-
~
~-
-100
·lO
'OAF
AF - OUTPUT \'OLTAGE
WITH DEEMPHASIS
II
I\.
·10
·lO
~M- L'PPR~SSIO~
\
.5O
I
SOk HZ. k. I.S'"
I-- l -
I
m.O
1
(T8A 720U onlyl
Fig. 8 AF output voltage and noise voltage v. input voltage (input
60n impedance, broadband)
203
TBA120T/TBA120U
61 • ~ SOkHl, k .3'!.
AF- OUTPUT VmlAGE
-
·20
! ."
.~ "
I~ J
.'-
I-
.
."
."
."
"' \
'mod alkHz
I
l
WITH
IOEETHAr
•"r"
Ii NOISE
AMPLIFIER)
OdB, UNf8,900mlJ ACR~SS IFIP.'N "\_____
'\\
I
-..... 1
/I~~~~E MEASURING
I I I I
T I - m.30'"
\
WITH COA S'S ~C
10
_V,
,
\1\
:' ."
-
\,:~I,
10
/~ \ .L1UION
.10
!
Il
.. " " "-J" " "
\
3011"
m.O
,
\
'"
i
--1-
-100
-liD -'00
·90
-80
-70
·60
·0;,0
(TBA 120T only)
Fig. 9 AF output voltage (pin 8), noise voltage and harmonic
distortion v. input voltage.
o
./
V
·20
I
1
,
~
/
V
~ ~.
UJINIJ
I
I
I
I
WITH ELECTROLYTIC CAPACITOR " .. F
FROM PIN 11 10 GROUND
-100
I
·110
o
OS
'·5
2
2.0;,
v,
1
'~~"1 v~
1 nJ
1
l·S
~
L·S
5
Vii
10
20
.
r-
,v'
v,
VPo!
·20
r-- r-r-- r-,o. - r--
Vi across IF
."
. .,
r;-
'"
m
/
-10
AF
1
,
V
."
". ."."
-T
-40 -30 -20
AVAF IdB)
'~,9'
I" I", ' I ~
.
32~~'
"
"
I I I
"
Fig. 10 Harmonic distortion v. volume control
I
1
OdS. v"F8' !-IS'"
/
-
". - - -
I
I
/
6
6-S
7
/
/
/
70S
R.lknl
Fig. 11 AF output voltage (pin 8) v. potentiometer resistance and
v. ratio of resistances
Fig. 12 AF output voltage (pin 8) v. voltage feeding into pin 5
V,RF = 60mVe ff, flF = 5,5 MHz, bf = ±150kHz, fmod
1kHz. Vee = 18V
VIDEO-RECORDER
'"
m
"'
BAIl7
"
"'co
'o----!i'" .
""
~2211
( •• 10'1)
11
f'
~ lJ8
Be
""i~
"'0
~
~
8C308
Function:
When switching voltage applied, the emitter follower
(BC238J on the output is blocked and the buffer stage
(BC308l is switched on. It includes a pre·emphasis to balance
the de--emphasis at the AF output. The I F amplifier is put out
of operation by the diode, BA127, and the 47kf! resistor.
The remote controllable volume regulator in the TBA120T!U
is used for recording and playback.
SOCKET (1)
1I·2k
8o.-r1'4
SOCKET (Ll
1·8k
'"
"
IT
SWITCHING
VOLTAGE:FOR PLAYBACK .12'1
FOR INPUT
Ne
SIMULTANEOUS INPUT ANO OUTPUT FOR AF
"
(1"
AF AMPLIFIER
Fig. 13 Circuit for direct connection to video recorders
204
=
CONSUMER
lVCIRCUITS
TBA440 NIp
VIDEO IF AMPUFIER DEMODULATOR
The TBA440 (TBA440N for NPN tuners, TBA440P for
PNP tuners) comprises a high-gain regulated video IF
amplifier, a controlled demodulator and 'two low-resistance
video outputs with positive and negative signal as well as
the complete key control and delayed tuner control.
IF liP (DIFFEAENTtAL)
IF IIP(D1FFERENTIALI
1
DECOUPLING
:2
OECOUPllNG
ov
3
WHITE LEVEL PRESET
CONTROL VOLTAGE QECOUPlING,
13
T8A 440
ABSOLUTE MAXIMUM RATINGS
Supply voltage steady
transitory
Voltage at pin 5
Voltage at pin 4
Voltage at pin 14
Operating ambient temperature
Total power dissipation
at T amb ';; 55°C
Ohmic resistance between pins 8 and 9
15V
16.5V
20V
5V
5V
-10° to +60°C
700mW
20n
v"
TUNER AGe
s
12
TUNER AGe THRESHOLD CONTROL
e.
GATING PULSE liP
7
SYNC. lEVEL CONTROL
DEMODULATOR TUNING
8
DEMODULATOR TUNING
:} VIDEO DIPs
DP16
Fig_ 1 Pin connections
FEATURES
•••
••
•
Complete Video I F in one Ie
High Sensitivity
Positive and Negative Video Signals
Gated AGC and Delayed AGC for Tuner
White and Black Levels Separately Adjustable
Ability to Control PI N Diode Attenuators
VIDEO
OUTPUTS
~
11--,I
I
I
I
I
I
I
I
9 }CEIo400ULATOR
I
TUNING
~--------------'~
I
5 ___
CONTROL
VOLTAGE
DECOUPLING
TUNER
AGe
L _ _ _ ..oL _______
TUNER
AGe
011
THRESI-fJLO
Fig. 2
7 __
JI
GATING
PlJLSE
INPUT
TBA440 block diagram
205
TBA440N / TBA440P
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated):
Tamb = +25°C
Vee = +13V
Reference point is pin 3 (OV)
Value
Characteristic
Pin
Supply voltage, Vee
Current consumption
DC output voltage
13
13
11
11
12
12
White level deviation
IWll Il;V I 3
l;VI 2/l;VI 3
Resistance R14-3 for l;VII = 1'1
AGC threshold V 10 = sync pulse
level for RI 0-1.1 = 0
Regulating slope R I o_ II Nll
Sync. pulse level with async. or
without gating pulses
Control current for tuner pre ar}ip.·
I F control voltage for max gain
for min gain
Gating pulse voltage
Residual I F voltage
Output current to earth
Output current to V I 3
Input impedance at max gain
at min gain
Input voltage for VII = 3V POp
Video bandwidth
AGC range
Intermodulation
13
40
5.1
6.2
1.1
2.5
15
52
6.1
10,11
10, 11
1.2
4.5
11
5
10
Vee = 15V
Vin = OV, RI4 = 00
Vin=OV,RI4=0
V in = OV, RI4 = 00
V in =OV, RI4 =0
V
VIO = Vll
knN
V
Vs > 2V, 10dB after AGC (TBA440P)
10d8 before AGC (TBA440N)
mA
0.5
5
-5
5
-1
1.8#2
1.9#0
100
7
58
55
V
mA
V
V
V
V
Conditions
kn
50
V
V
V
mV
mA
mA
kn#pF
kn#pF
}1V Input 60n via 3:5 transformer
MHz
dB
dB
Input 0.3 to 1.5V POp
II
II
IS
~
HH-+++-+-H-+++-l
/
.
;; I-iH4+-f-+ :~~:,::
,/
Vl1
=]V
I
1-+,--roo
.. 36t.4Hz
.61
• 3104Hz
f-+-
RG
= soon.
t--t--
VCC: 15V
,
I
I
0
HI
20
30
AttENUATION IdBI
'0
"
Fig. 3 Noise figure v. attenuation
(measured at video frequency)
206
1.8
0.2
i5
0
2.5
-2
52
10
z
10.5
28
4.1
05
4
4
7
11, 12
11,12
11, 12
1
1
1
"
"
u.
Max.
0.15
0.05
1
16
-
Typ.
11, 13
12,13
14 3
,
~
Units
Min.
~
1.0
(
:3SMHz
~H-++-f-+ RGRSOOA
o·,I-iH-++-+-+-H-++-H
OO~~IO=t~20~=,tO:t~~=t~'~O~60'
ATTENUATION (dBI
Fig. 4 Control voltage v. attenuation
TBA440N / TBA440P
20
20
16
I
---/
./
18
:?~
'\
"
I I
"'\ , \
.......
........
--r-. '\
\ \
\
11
;;
1,0
.s
2,Sk
RS:Uk
1·9k
1-4k
O'15k
10
0
5·5k
R6,e'Ok
o
o
-zo
10
I
30
40
SO
10
60
20
4-Sk
). 9k
\ i \.- \.
30
400
loOk
0
\
50
60
ATTENUATION IdB)
ATTENUATION (dBI
Fig. 5 Tuner control current v. attenuation with R6 as parameter
(TBA440P)
Fig. 6 Tuner control current v. attenuation with f!6 as parameter
(TBA440N)
I
I
TUNER DU ....My
~. ~1rtl21~
~~'-~21
". IJ;
I
1221
L2
t-;t-~!.-..t--C'-'-h
39p
FOR CCIR ONLY
,--------------_._-----------ZF
I
I
,
•
11 TBA440P FOR PNP JU',ER
I:O,TUNER:MAX GAIN!
-_._---
~'II
- - - - - . --~-~--- ... -. • [21
t
1'2k
1·21<
+
l:l0mA !TUNER"MIN GAIN!
21 TBA 4LON FOR NPN TUNER
hl0mA [TUNER MAX GAINI
I:OITUNER: MIN GAIN!
PNP TUNER PREAtoIP
NPN TUNER PREAMP
Fig. 7 IF application with TBA440P or TBA440N for CCIR standard (values in brackets for U.S. standard)
207
/
208
CONSUMER
TVCIRCUrrs
TBA530
RGB MATRIX PRE-AMPUFIER
The TBAS30 is an integrated R-G-B matrix
pre-amplifier for colour television receivers incorporating a
matrix pre-amplifier for R-G-B cathode or grid drive of
the picture tube without clamping circuits. The chip layout
has been designed to ensure tight thermal coupling between
all transistors in each channel to minimise thermal drifts
between channels. Also, each channel follows an identical
layout to ensure equal frequency behaviour of the three
channels.
This integrated circuit has been designed to be driven
from the TBAS20 synchronous demodulator integrated
OUTPUT LOAD
RESISTOR(BLUESIGNAt!
!
-IB-YlINPUT
2
-!a-V! INPuT
1
- (R-Y\INPUT
L
LUMINANCE INPUT [ 5
-
1&
BLUE SIGNAL OUTPUT
BLUE CHANNEL fEEDBACK
OUTPUT LOAD RESISTOR (GREEN SIGNAL}
~~~
GREEN SIGNAL OUTPUT
\l
GREEN CHANNEL FEEDBACK
12
ov [ ,
CURRENT FEED POINT
7
OUTPUT LOAD RESISTOR (REO SIGNAU
10
RED SIGNAl OUTPuT
Vee
RED CHANNEL feEDBACK
~_....J'
circuit.
OP16
ABSOLUTE MAXIMUM RATINGS
Fig. 1 Pin connections
Supply voltage, Vee
13.2V
Supply currents:10mA
11 = 111 = 114 max
SOmA'
11 0 = 11 3 = 11 6 max
Total power dissipation
400mW'
at Tamb = 60°C, PTOT
-SS to +12SoC
Storage temperature
-10 to +60°C
Operating ambient temperature
At increased voltages due to external failures (e.g.,
collector-base breakdown in the output transistors) a
maximum current of SOmA is permitteq between
pins 16 and 8, 13 and 8, 10 and 8. The maximum
permissible power dissipation is then SOOmW .
QUICK REFERENCE DATA
•
•
Supply Voltage (Nominal) 12V
Total Supply Current
(Nominal)
30mA
•
Operating Ambient
Temperature Range
•
-10 to +60°C
Gain of Luminance and
. Colour-difference Channels
(Typ.)
100
.,
11
10
Fig. 2 TBA530 block diagram
209
TBA530
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):Vee = +12V, Tomb =+25°C
Black level: VR_Y = VG_Y = VB_Y = 7.5V
Vy = 1.5V
Reference = pin 6
Value
Characteristic
Symbol
Min.
Gain of colour channels (B-Y,
G-Y, R-Y)
Conditions
-
f = 0.5M Hz (see note 1)
0.9
-
-
1.1
VR
VG
VB
140
140
140
V
V
V
R2
R3
R4
60
60
60
kfl
kfl
kfl
f = 1kHz
C2
C3
C4
3
3
3
pF
pF
pF
f = lMHz
Rs
20
kfl
f
= 1kHz
Cs
B
IT'OT
10
6
30
pF
MHz
mA
f
= lMHz
I nput resistance of colour
difference amplifiers
I nput capacitance of colour
difference amplifiers
Input resistance of luminance
Qrnplifier
Input capacitance of luminance
amplifier
3dB bandwidth of all channels
Total current drain
Units
Max.
100
100
100
G2
G3
G4
Ratio of gain of luminance
amplifier to colour amplifiers
DC output voltages
Typ.
See note 2
NOTES
1.
2.
G is defined as the voltage ratio between the input signals at the pins 2, 3, 4 and the output signals at the collectors of the output
tran!;istors.
At.the collectors of the output transistors. The value of this voltage is also dependent on the external circuitry.
rI
I
"
"
-,
10'
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I'
I
L_
I
., .
OV
Fig. 3 TBA530 circuit diagram
210
__
I
TBA 530 :
~_J
r-~r-_-_~~~_-_~~
'I:c
TBA530
-8 OUTPUT
-G OUTPUT
- R OUTPUT
lODV B-W
100V B-W
10010' B·W
200j.lH
r-----~r_--4_------------~------~--~------------~------~--_+----r_~~--o+200V
~,Ik
!In
5'5W
S-5W
-IG-Y)
,,.
ssw
Y SIGNAL
IV B-W
Fig. 4 Typica/application diagram
211
TBA530
FUNCTIONAL DESCRIPTION
Pin
1. Output load resistor, blue signal
(Also pins 11 and 14 for red and green signals
respectively.) Resistors (47kQ, lW) connected to
+200V provide the high value loads for the internal
amplifying stages. The nominal operating potential on
these pins is defined by the IC and the DC feedback
and is approximately +SV. The maximum current
which can be allowed at each of these pins is 10mA.
2. -(S- Y) input signal
This signal is fed via a low·pass filter from the TSAS20
demodulator IC (pin 7) having a DC level of about
+7.5V. The input resistance for this pin is typically
60kQ with an input capacitance of less than SpF
(similarly for pins 3 and 4).
3. -(G-Y) input signal
The DC black level of this signal is about +7.SV. (See
pin 2.)
4. -(R-Y) input signal
The DC black level of th is signal is about +7 .SV. (See
pin 2.)
S. Luminance signal input
The DC level on this pin for picture black is +1.6V.
The required signal amplitude is 1 V black·to·white
with negative-going syncs (or blanking) for cathode
drive as shown. The input resistance at this pin is 20kQ
approximately with a capacitance of less than lSpF.
6. Negative supply (earth).
7. Current feed point
A current of approximately 2.SmA is required at this
pin, fed via a 3.9kQ resistor from +12V, to bias the
internal differential amplifiers. A decoupling capacitor
of 4. 7n F is necessary.
S. Positive 12V supply
Maximum supply voltage permitted, 13.2V. Current
consumption approximately 30mA.
9. Red channel feedback (green channel, pin 12; blue
channel, pin 15)
The DC working points and gains of both the output
stages and the IC amplifier stages are stabilised by the
feedback circuits. The black level potentials at the
collectors of the output stages (tube cut-off) are
adjusted by setting correctly the DC levels of the
colour difference signals produced by the TBAS20
demodulator IC. The gains of the R-G-B output
stages are adjusted to give the correct white points
setting on the picture tube by adjusting the
potentiometers in the feedback paths (RV1, RV2).
212
10. Red signal output (green and blue signal outputs on 13
and 16)
These pins are internally connected with pins 11, 14
and 1 respectively via zener type junctions to give a DC
level shift appropriate for driving the output transistor
bases directly. To by-pass the Zener junctions at HF
three 10nF capacitors are required.
11. Output load resistor, red channel (see pin 1).
12. Green channel feedback (see pin 9).
13. Green signal output (see pin 10).
14. Output load resistors, green channel (see pin 1).
lS. Blue channel feedback (see pin 9).
16. Blue signal output (see pin 10).
OPERATING NOTES
Careful attention to earth paths should be given,
avoiding common impedances between the input (decoder)
side and the output stages. Also, to enable matched
performance to be achieved, a symmetrical board and
component layout should be adopted for the three output
stages. To compensate for the effect upon HF response of
inevitable differences the compensating capacitors C, and
C2 and C3 may be appropriately selected for any given
board layout.
The signal black level at the collectors of the R-G-B
output stages depends upon the + 12V supply, the DC level
of the colour difference signals from the TSAS20
demodulator IC and the black level potential of the
luminance signal applied to the TBAS30 matrix IC. The DC
levels of the signals produced and handled by the IC's are
designed to have approximately proportional tracking with
the 12V supply potential,
.
I.e.,
leN (DC level, signal) ~ Vnom (DC level, signal)
IN12V
12
To ensure that changes in picture black level due to
variations on the lev supply to the IC's occur in a
predictable way, all the IC's should be operated from a
common supply line. This is specially important for the
TBAS20 and TBAS30. Furthermore, to limit the changes in
picture black level during receiver operation, the 12V
supply should have a stability of not worse than ±3% due to
operational variations.
To reduce the possibility of patterning on the picture
due to radiation of the harmonics of the products of the
demodulation process, the leads carrying the drive signals to
the picture tube should be as short as the receiver layout
will allow. Resistors (typically 1.5kQ connected in series
with the leads and mounted close to the collectors of the
output transistors provide useful additional filtering of
harmonics.
CONSUMER
lVCIRCUITS
TBA540
REFERENCE COMBINATION
The TBA540 is an integrated reference oscillator circuit
for colour television receivers incorporating an automatic
phase and amplitude controlled oscillator employing a
quartz crystal, together with a half-line frequency
synchronous demodulator circuit. The latter compares the
phases and amplitude of the swinging burst ripple and the
PAL flip-flop waveform, and generates appropriate ACe,
colour killer and identification signals. The use of
synchronous demodulation for these functions permits a
high standard of noise immunity.
OSCILLATOR FEEDBACK liP
~~Dov
AEACTANCE CONTROL STAGE FEEDBACK
1
Vee
J
REFEAENCE WAVEFORM DiP
8URSTWAVEFQRM liP
ISp OSCILLATOR FEEDBACK
"
I.
TBA 540 13
\
12
REFEAENCEWAVEFOAM liP
,
COLOUR KILLER O/P
1
PAL fLIP/FLOP SOUARE WAVE liP
6
I'
P 1,
P
DC CONTROL POINTS FOR
OSCILLATOR PHASE CONTROL
,LOOP
~
b
IO~
9b
ACe LEVEL SETTING ISEE PIN 10)
Ace GAIN SETTING
Ace LEVEL SETTING ISEE PIN 1,1
Ace OIP& tDENT
DP16
QUICK REFERENCE DATA
III
Supply Voltage, V3-16
Fig. 1 Pin connections
ABSOLUTE MAXIMUM RATINGS
12V (Nom.1
III Total Current Drain, 13 38mA (Typ.1
II R-Y Ref. Output, V 4-16 l.4Vpp (Typ.1
II Colour Killer Output, V7-16
II
Colour ON : 12V (Typ.1
Colour OFF: 250mV (Max. I
ACC Output Voltage, V9.16:at Correct Phase of PAL Switch: +0.2 to
+4V
at Incorrect Phase of PAL Switch: +4 to
+11V
Voltages arc referred to pin 16
Electrical
Supply voltage V3 (Veel
Total power dissipation
at Tamb = +60 o e
Surge current, minimum
duty cycle 10:1, 17max
13.2V
700mW
50mA
Temperature
Storage temperature, T st
Operating temperature, 'ram b
_55°C to +125°e
-lOoe to +60 oe
~-+-+-+--4"
Fig. 2 TBA540 block diagram
213
TBA540
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated):
Vee (V3) = +12V, Tamb = +25°C, Vs = 1.5Vp·p burst, Va
Voltages referred to pin 16
= 2.5Vp·p PAL square wave.
Value
Characteristic
Output Signals
B· Y reference signal output
Colour killer output
colour 'on'
colour 'off'
ACC output signal range
at correct phase of PAL switch
at incorrect phase of PAL switch
Oscillator Section (Amplifier)
Input resistance
Input capacitance
Voltage gain, G1S.l
Reactance Control Section
Voltage gain, G1S.2
Rate of change of gain with phase
- difference between burst
and reference signal, LlG 1S. 2
--L\rp5·4
4
7
Min.
Typ.
Max.
1
1.4
2
Vp·p
12
100
250
V
mV
9
+4 to +0.2
+4 to +11
V
V
15
15
15·1
3.5
5
4.7
kn
pF
15·2
1.3
15·2
5
FUNCTIONAL DESCRIPTION
Functions listed by pin number
1, Oscillator Feedback Output
The crystal receives its energy from this pin. The output
impedance is approximately 2kn in parallel with 5pF.
2. Reactance Control Stage Feedback
This pin is fed internally with a sinewave derived from
the reference output (pin 4) and controlled in amplitude by
the internal reactance control circuit. The phase of the
feedback from pin 2 to the crystal via Cl is such that the
value of Cl is effectively- increased. Pin 2 is held internally
at a very low impedance therefore the tuning of the crystal
is controlled automatically by the amplitude of the
feedback waveform and its influence on the effective value
ofCl.
3. Positive l2V Supply
The maximum voltage must not exceed 13.2V.
4. Reference Waveform Output
This pin is driven internally by the regenerated
subcarrier waveform in B·Y phase. (The output is in B·Y
rather than R· Y phase as the burst phase network produces
a lag of 90° of the burst applied to pin 5.) An output
amplitude of nominally 1.4V peak·to·peak is produced at
low impedance. No DC load to earth is required. A DC
connection between pins 4 and 6 is, however, necessary via
the bifilar coupling inductor. The function of this inductor
is to produce, on- pin 6, a signal of equal amplitude and
opposite phase (.)B·Y)) to that on pin 4. A centre tap on
the inductor, connected to earth via a DC blocking
capacitor, is therefore necessary.
214
Conditions
Units
Pin
Pins 13 and 14 interconnected
rad-I
5. Burst Waveform Input
A burst waveform amplitude of 1.5V peak·to·peak is
required to be AC coupled to this pin. The amplitude of the
burst will normally be controlled by the adjustment and
operation of the ACC circuit. The input impedance at this
pin is approximately lkn and a threshold level of 0.7V
must be exceeded before the burst signal becomes effective.
A DC bias of 400mV is internally derived for pin 5.
The absolute level of the tip of the burst at pin 5 will
normally reach 1.5V.
6. Reference Waveform Input
This pin requires a reference waveform in the ·(B·Y)
phase, derived from pin 4 via a bifilar transformer (see
pin 4), to drive the internal balanced reactance control
stage. A DC connection between pins 4 and 6 must be made
via the transformer.
7. Colour Killer Output
This pin is driven from the collector of an internal
switching transistor and requires an external load resistor
(typically 10kn) conhected to +12V. The unkilled and
killed voltages on this pin are then +12V and <250 mV
respectively. (The voltage range on pin 9 over which
switching of the colour killed output on pin 7 occurs is
nominally +2.5V.)
8, PAL Flip-Flop Square Wave Input
A 2.5V peak·to·peak square wave derived from the PAL
flip·flop (in the TBA520 or TBA990 demodulator IC) is
required at this pin, AC - coupled via a capacitor. The
input impedance is about 3.3kn.
TBA540
9. ACC Output
An emitter follower provides a low impedance output
potential which is negative-going with a rising burst input
amplitude. With zero burst input signal the DC potential
produced at pin 9 is set to be +4V (RV1). The appearance
of a burst signal on pin 5 will cause the potential on pin 9
to go in a negative direction in the event that the PAL
flip·flop is identified to be in the correct phase. The range
of potential over which full ACC control is exercised at
pin 9 is determined by the control characteristic of the
ACC amplifier, i.e., for the TBA560 from O.B to 1V. The
potential on pin 9 will fall to a value within this range as
the burst input signal is stabilised to an amplitude of 1.5V
peak·to·peak. The latter condition is achieved by correct
adjustment of RV2. If, however, the PAL flip·flop phase is
wrong the potential on pin 9 will move positively. The
potential divider R5, R6 will then operate a PAL switch
cut·off function in the TBA520 demodulator IC.
Two 2% tolerance 10k resistors with the addition of a
270n resistor at pin 13 are used in place of the previous
balancing network. The 270n resistor may be modified
according to the nature of the noise that appears at pin 5.
The filter network consists of R2, C2, C3 and C4. The
DC potentials on these pins are nominally +6V.
15. Oscillator Feedback
The input impedance at this pin is nominally 3.5kn in
parallel with 5pF. No DC connection is required on this
pin. The voltage gain in the Ie between pins 15 and 1 is
nominally 4.7 times.
16. Negative Supply (earth).
OPERATING NOTES
Performance and Comments
11. ACC Gain Control
Initial adjustment
(a) Remove burst signal.
(b) Short·circuit pins 13·14. Adjust oscillator to correct
frequency by Cl.
(c) Set the ACC level adjustment RV1, to give +4V on
pin 9. Remove short circuit.
(d) Apply burst signal.
(e) Adjust ACC gain, RV2, to give a burst amplitude of
1.5V peak·to·peak on pin 5.
RV2 is adjusted to give the correct amplitude of burst
signal on pin 5 (1.5V peak·to·peak) under ACC control.
4322 1520110)
10. ACC Level Setting
The network connected between pins 10 and 12
balances the ACC circuit and RV1 is· adjusted to give +4V
on pin 9 with no burst input signal to pin 5. C5 provides
filtering.
12. See
Pin 10.
13. See
Pin 14.
14. DC Control Points in Reference Control Loop
Pins 13 and 14 are connected to opposite sides of a
differential amplifier circuit and are brought out for the
purpose of DC balancing of the reactance stage and the
connection of the bandwidth-determining filter network.
Phase lock loop performance (with crystal type
(a) Phase difference between reference and burst signals
for ±400Hz deviation of crystal frequency, ±10o.
(b) Typical holding range, ±600Hz. (c)
(c) Typical pull·in range ±300Hz.
(d) Temperature coefficient of oscillator frequency, only
2Hz/oC maximum.
COLOUR KILLER
REFERENCE OUTPUTS
B'Y
R-Y
- B-Y
2',.
'"
21
OUTPUT IT BA S60 I
12k
+1111
Hf2 INPUT
[TSA 520,1)'01
10k
33"
)30",1
220
BURS~I-'
INPUT
-r-.1 ~
J/!. ·--=;'f!:~~~lIlJ
r
BURST PHASE.
I DENT OUTPUT
11BA990t
Ace OJTPUT
ITBA560t
10k
tDENT OUTPUT
l't.
IT8A5201
2'/.
.1211
",
6 311
Fig.. 3 Typical application diagram
215
216
.~!
CONSUMER
TV CIRCUITS
TBA560 C
LUMINANCE AND CHROMINANCE COI\ITROL COMBINATION
The TBA560C is an integrated circuit for colour
television receivers incorporating circuits for the processing
and control of the luminance and chrominance signals. It
can be used in conjunction with the TBA520 or TBA990,
530, 540, 550 and TCABOO integrated circuits.
The luminance part provides luminance delay line
matching, DC contrast control, black level clamp circuit,
brightness control and flyback blanking.
The chrominance part provides chroma amplification
with ACC, DC chroma gain control which tracks with the
contrast control, separate saturation control, burst gate,
chroma signal flyback blanking colour killer and PAL delay
line driver.
The TBA560C is not an equivalent of the TBA500 and
510 although it performs similar functions to those circuits.
8ALANCED CHAOMA INPUT
1
---;
OC CONTRAST CONTAOL
2
1,
LUMINANCE INPUT
1
l'
BLACK LEVEl CLAMP CAPACITOR
LUMINANCE OUTPUT
, TeAS6QC "
.,
BALANCEO CHAm.IA INPUT
ACC INPUT
CHROMA SATURATllJN CONTROL
DC FEEDBACK fOR CHROMA CHANNH
BRIGHTNESS CONTROL
V"
10 " BURST GATE AND CLAMPING PULSE III'
BURST OUTPUT _ __ J
Fl VBACK BLANKING WAVEfORM
g
CHROMA OUTPUT
DP16
F;g. 1 Pin connections
ABSOLUTE MAXIMUM RATINGS
QUICK REFERENCE DATA
Voltages are referred to pin 16
Electrical
V, 1 max.
V,
V2
o to +6V
V.
o to +3V
Vs
-5 to +5V
Va
Supply voltage (note 1)
Oto +5V
V'O min.
0'0 +12V (note 21 V,2
V'3
V14 min.
V,s
13.2V
-SV
-5 to +6V
-3 '0 +6.SV (note 2)
-SV
o to +lmA
13
-1 to +3mA
-5 to OmA
-1 to +lmA
1'5
-3 to +2.,..A
Total power dissipation
T amb :;: 60°C (note 1)
15
IS
I,
Ptotrnax.
19
I,Omax
l 14 max,
..
-10 to OmA
+3mA
+lmA
Oto +lmA
560mW
T einperature
Storage temperature
Operating ambient temperature
..
o to +5V
Currents (positive when flowing into the integrated circuit)
I,
..
..
..
-SS"c to +12S"C
-10"C to +60"C
..
..
..
..
..
Supply Voltage (Nom.) IV 11.(6) 12V
Supply Current (Nom) (111) 30m A
Luminance Signal Input Current (Typ.)
113Ip.p)) OAmA
Luminance
Output Signal at Nominal
Contrast Setting ITyp.) and Input Current as
Above IV5-16Ip.p)) 1V (See Note 1)
Chrominance
Input
Signal
IMin.)
(V'.15Ip.p)) 4mV
Chrominance Input Signal (Max.) V'·'5Ip·p))
80mV
Chrominance Output Signal at Nominal
Contrast and Saturation Setting (Typ)
IV9.l6Ip-p)) lV(See Note 1)
Contrast Control Range ;;.20dB
Saturation Control Range ;;.20dB
Burst Output (Closed ACC Loop) ITyp)
(VJ.16Ip.p)) lV
Notes
1. Permissible during receiver switch on transient V 11 max. l6V.
Ptolmax.
700mW for t;;-14dB. A similar variation in gain in the chroma
channel occurs in order to provide the correct tracking
between the two signals. Beam current limiting can be
applied via the contrast control network as shown in the
peripheral circuit, when a separate overwind is available on
the line output transformer.
3. Luminance Signal Input
greater than -1 V negative excursion, or DC coupled pulses
of similar amplitude whose negative excursion is at zero
volts DC are applied, the signal level at the luminance
output (pin 5) during blanking will be OV. However, if the
blanking pulses applied to pin 8 have an amplitude of -2 to
-3V the signal level at the luminance output during
blanking will be +1.5V. The negative pulse amplitude
should not exceed -5V_
9. Chroma Signal Output
With a 1 V peak-to-peak burst output signal (pin 7) and
at nominal contrast and saturation setting (pins 2 and 13)
the chroma signal output amplitude is 1V peak-to-peak. An
external network is required which provides DC negative
feedback in the chroma channel via pin 12_
10. Burst Gating and Clamping Pulse Input
A positive pulse of not less than 50l1A is required on this
pin to provide gating in the burst channel and luminance
channel black-level clamp circuit. The timing and width of
this current pulse should be such that no appreciable
encroachment occurs into the sync. pulse or piclUre line
periods during normal operations of the receiver.
11. +12V Supply (Vee)
a current sink. The luminance signal from the delay line is
fed via a series terminating resistor and a DC blocking
capacitor and requires to be about OAmA peak-to-peak
amplitude. A DC bias current is required via a 12kn resistor
to the +12V line.
Correct operation occurs within the range 10.8 to
13_2V _ All signal and control levels have a linear
dependency on supply voltage but, in any given receiver
design this range may be restricted due to considerations of
tracki ng between the power supply variations and picture
contrast and chroma Ip.vels. The power dissipation must not
exceed 5BOmW at 60°C ambient temperature.
4. Charge Storage Capacitor for Black Level Clamp
12. DC Feedback for Chroma Channel (see pin 9)
5. Luminance Signal Output
13. Chroma Saturation Control
This terminal has a very low input impedance and acts as
a
An emitter follower provides
low impedance output
signal of 1 V black-to-white amplitude at nominal contrast
setting having a nominal black level in the range 0 to +2.7V.
An external emitter load resistor is required, not less than
lkQ_ If a greater luminance output is required than lV.
with normal control settings, the input current swing at
pin 3 should be increased in proportion.
6. Brightness Control
Over the range of potential +0.9 to +1 JV the black level
of the luminance output signal (pin 5) is increased from 0
to +2_7V. The output signal black level remains at +2.7V
when the potential on pin 6 is increased above +1.7V.
7. Burst Output
A control range of +6d8 to>-14dB is provided over a
range of DC potential on pin 13 from 6_2 to 2_7V. Colour
killing is also achieved at this terminal by reducing the DC
potential to less than +1V, e.g., from the TBA540 colour
killer output terminal. The minimum "kill factor" is 40d8.
14. ACC Input
A negative-goi ng potential gives an ACe range of about
26dB starting at +1.2V_ From lV to 800mV the steepest
part of the characteristic occurs, but a small amount of gain
reduction also occurs from BOOmV to 500mV. The input
resistance is at least 50kSl.
15. Chroma Signal I nput (see pin 1)
16. Negative Supply, OV (Earth)
A 1 V peak-to-peak burst (controlled by the ACC
system) is produced here. Also, to achieve good DC
stability by negative feedback in the burst channel the DC
potential at this pin is fed back to pins 1 and 15 via the
chroma input transformer.
219
TBA560C
,
...
,.
-r--
/
-
v.- \-
I
: I
,
CURVES~
I
II
I
LIMlT OF CONTROL
,I-- ~
'" H-l-++HH++-.j..,.jl,.,j.-+~
'''It-o1
I II I
11
LlNlTS OF V,-I' -At WHICH SO"'. GAIN
I
I
I
REDUCTION IS QI!ITAINEO
,
I
/ I
lNOWINAL CONTRASJ)
:
I
;t II
I
I t
0
0
>S
•
Vz -16 [V)
Fig. 3 Contrast control characteristic
(luminance amplifier;
Fig. 4
Control of black {five/at output
Fig. 5
ChrominancfJ amplifi6f S8tufation
characteristic
of luminance Dmplifief
.
BRIGHTNESS
CONTROL
~--4---- BL.4.NKING
V
COMPOSITE
'(IDEO INPUT
FROM TCAno
".
OUTPUT
1'~_-+==::j:=t:=:CHROM'"
L
e",cl( PORCH
,-~-~:c::;::;:==:!=~===~==±==~~~=====~=~=~-~
BEAN CURRENT
(E~:;~~GE~rg'~~
_--+-----<
EHf OVERWIND!
Fig. 6 Application diagram
220
COlOU~ KILLER
/I.
PULSE
CONSUMER
TV CIRCUITS
TBASOO
5W AUDIO AMPUFIER
The TBA800 is a robust high efficiency audio amplifier
especially designed for Television Receivers.
FEATURES
•
•
Wide Supply Voltage Range
High Efficiency
•
•
Low Cost
Second Source Availability
RP12
ABSOLUTE MAXIMUM RATINGS
Fig. 1 Pin connections
Supply voltage
Peak load current
Power dissipation
Pin 1 or 3
Pin 12
vee
30V
1.5A
QUICK REFERENCE DATA
5W (case temp 90°C)
Operating temperature (with 2SoC/W heat sink)
_lOoe to +6SoC
Junction temperature
150°C
Storage temperature
_25°C to +125°C
•
•
•
Supply Voltage Range: 5 to 30V
Efficiency at 4W: 70%
Power Into 16n Load (Vee = 24V): 5W
12
10
Fig. 2 TBA800 circuit diagram
221
TBA800
ELECTRICAL CHARACTERISTICS
rest Conditions (unless otherwise stated):
Tamb = +25°C
Vee = 24V Rf = 56n RL = 16n frequency 1 kHz
Reference point i.s pin 9
Measurements made in typical application circuit, Fig. 8
Value
Characteristic
Pin
Supply voltage Vee
Quiescent output voltage
Quiescent current
Input current
Output power
Input voltage
Input impedance
3dB bandwidth
Total harmonic distortion
Open loop gain
Closed loop gain
Input noise voltage
I nput noise current
Efficiency
Thermal resistance
1,3
12
1,3
8
12
8
8
Units
Min.
Typ.
Max.
5
11
24
12
9
1
5
80
5
40 to 20k
0.5
70
42
5
0.2
70
30
13
20
5
4.4
12
39
8
B
THO = 10"J.
t ,,1KHz
Rf .560
45
V
V
mA
Il A
W
mV
Mn
Hz
%
dB
dB
70
12
Il V
nA
%
°C/W
°C/W
,
Conditions
10% THD
Output power 5W
o/ppower 50mWto2.5mll'l
Rf=On
Rf = 56n
40Hz to 20kHz
Output power 4W
Junction to ambient
Junction to fin
I
I
Vcc • 21.V
Rl" 160
I
I
f" lkH2
RI" 560
6
u
~
~
~
~
a
,
1/
<
a
~
<
~
2
J
10
20
Vcc IV}
Fig. 3 MaJ(. available output power v. supply voltage
222
OUTPUT POWER
I W)
Fig 4 Total harmonic distortion v. output power
TBA800
1
\RlhJC
z
1\
o
:i
~
J
C
w
u
~
0,
~lhJA
~
.........
o
-,0
'0
\
\
N
100
Vet (V)
Tamb t"C)
Fig. 6 Max, dey/co power dissipation v. supply voltage
Fig. 5 Ds"vice power dissipation v. ambient, temperature
f-
Vee' HV
Rl" 160
Rt • ~60
z
o
f-
r-
~
~
J
C
r-
50mW
,
<
o
2-5W
I
o
101
Fig. 7 Total harmonic distortion v. frequency
223
TBA800
CIO
VINo---J~.----------'-I
0·'11
11
FINS
R,
C2
500IJ
lOOk
RI
56
The supplv voltage must be disconnected before inserting the integrated circuit into the socket.
Fig. 8 Tvpical application
APPLICATION NOTE
When using a supply of 10V or less, pin 3 should not be
connected and the bootstrap capacitor C8 should be
omitted.
224
CONSUMER
TV CIRCUITS
TBA920
TBA920S
LINE OSCILLATOR COMBINATION
The TBA920 is a silicon integrated circuit designed for
TV receiver applications. It accepts the composite video
signal, separates sync. pulses with the added safeguard of
noise gating and provides a sync. output for the vertical
integrator. Also incorporated is the line oscillator together
with two phase comparators: one to compare flyback
pulses to the oscillator and the other for sync. phase
comparison. The TBA920S is a special selection of the
TBA920 (see Electrical Characteristics).
HORIZONTAL OUTPUT
2
15
FREQUENCY Q)NTROl
PHASE SHIFTER INPUT
3
14
OSCILLATOR CAPAcnOR
PHASE COMPARATOR 2 OUTPUT
,
IJ
DECOUPliNG
HORIZONTAl FL'(BACK PULSE rNf'UT
5
12
CONTROL VOLTAGE OUTPUT
PHASE COMPARATOR 1 INPUT
6
II
TIME CONSTANT FILTER
SYNC SEPARATOR OUTPUT
7
10
COINCIDENCE FILTER
VIDEO INPUT
8
NOISE GATE IhtPUT
DP16
Fig. 1 Pin connections
FEATURES
•
Sync separator
ABSOLUTE MAXIMUM RATINGS
•
•
•
•
Noise Gate
Line Oscillator
Dual Phase Comparator
Suitable for Thyristor or Transistor Systems
Reference point is pin 16 unless otherwise stated
QUICK REFERENCE DATA
•
•
•
•
•
Supply Voltage (nom.)
Supply Current (nom.)
Video IfP (+ve Sync.)
Flywheel PUll-in Range
Output Current
12V
36mA
3V
±lkHz
20mA
Supply voltage, Vcc
Voltage at pin 3, V3
Voltage at pin 8, -Va
Voltage at pin 10, V,o
Average current pin 2, '28V
Peak current, pin 2, '2pk
Peak current. pin 5. ISpk
Peak current. pin 7, 17pk
Peak current, pin 8. lapk
Peak current, pin 9, 19pk
Total power dissipation. PIOI
Storage temperature, T51g
Operating ambient temperature, Tamb
COI4.5V, V.>1.5V
V,o<2V, V.>1.5V
Time coincidence between sync. pulse
and flyback pulse or V I .>4.5V
No time coincidence or V I .<21/
See note 2
D.jl/. = ±3% (D.j=470Hz), see Fig. 3
See Fig. 3
Control Loop II (Between Flyback
Pulse and Oscillator)
Permissible
leading edge
(pin 2) and
flyback pulse
Static control
delay
between
of output pulse
leading edge of
Idtot
b.t
error
0.5
Tt;
Peak output
lIyback pulse
current
See operating noles (3)
%
during
14pk
±0.7
mA
t
b.t
4.9
JlS
See operating notes (4)
JlS
See operating notes (51
See operating notes (5)
Overall Phase Relation
Phase relation between leading
edge of sync. and middle of
lIyback pulse
Tolerance of phase relation
TBA920
TBA920S
Voltage for t2 = 12 to 32tJs
Adjustment sensitivity
flt,
Input current
flV,
13
External Switch·over or Parameters
(Loop Filter and Loop Gain) of
Control Loop I (e.g. for Video
Recorder Application). See Note 3
Required switch·over voltage
±0.7
±O.4
V3
6 to 8
V
10
tJslV
2
NOTES
I. Exclusive
Of
I
JlA
,
V,.
4.5
2.0
Required switch·over current
tJs
I, •
80
120
V
V
tJ A
JlA
R"
RII
A"
A"
= 150n
= 2kn
= 150n, V, 0 = 4.5V
= 2kn, V,. = 2.0V
external component tolp.rances
2. Adjustable with AU"IS
3. With sync. pulses at pins 7 and 8; without RC network at pin 10
227
TBA920/TBA920S
OPERATING NOTES
1. The output pulse duration is adjusted by shifting the
leading edge (V J from 6V to 8V). The pulse duration is a
result of delay in the line output device and the action of
the second control loop in the TBA920.
For a line output stage with a BU108 high voltage transistor
the resulting duration is about 22/ls, and in such a way that
the line output transistor is switched on again about 8/ls
after the middle of the line flyback pulse. This pulse
duration must be taken into account when designing the
driver stage and driver transformer as this way of driving
the line output device differs from the usual, i.e. a driver
duty cycle of about 50%.
2. The oscillator frequency can be changed for other TV
standards by an appropriate value of Ct •.
3. The control error is the remaining error in reference to
the nominal phase position between leading edge of the
sync. pulse and the middle of the flyback pulse caused by a
variation in delay of the line output stage.
4. This phase relation assumes a luminance delay line with
a delay of 500ns between the input of the sync. separator
and the drive to the picture tube. If the sync. separator is
inserted after the luminance delay line or if there is no
delay line at all (monochrome sets). then the phase relation
is achieved at Cs = 560pF.
5. The adjustment of the overall phase relation and
consequently the leading edge of the output pulse at pin 2
occurs automatically by the control loop II or by applying
a DC voltage to pin 3.
228
posITIve
NOISE PULSES
FORVIOEORECOROER
AI"PLICATIOO
Fig. 3 Application diagram
CONSUMER
TV CIRCUITS
TBA950:2X
UNE OSCILLATOR COMBINATION
The TBA950 :2X is a monolithic integrated circuit
for pulse separation and line synchronisation in TV
receivers with transistor output stages.
The TBA950 :2X comprises the sync. separator with
noise suppression, the frame pulse integrator, the phase
comparator, a switching stage for automatic changeover
of noise immunity, the line oscillator with frequency
range limiter, a phase control circuit and the output
stage.
It delivers prepared frame sync. pulses for triggering
the frame oscillator. The phase comparator may be
switched for video recording operation. Due to the
large scale of integration few external components are
needed.
.
ov'
LINE DIP, DRIVE
2
V~,
3
PHASE COMPARATOR TIME CONSTANT
t
'"
TBA
"
LINE fREQUENCY PRESET
13
LINE FREQUENCY CAPACITOR
12
950:2X 11
PHASE CONTROL CAPACITOR
PHASE PRESET
SYNC SEPARATOR liP
5
10
LINE FlYBACK PULSE liP
COMPOSITE SYNC DIP
Eo
9
TIME CONSTANT SWITCH DiP
fRAME SYNC DIP
"1..'_ _ _'.r SWITCH DELAY CAPACITOR
DP14
Fig. 1 Pin Connections
O,33~
f
VIDEO
INPUT SIGNAL
Fig. 2 Block diagram and test circuit
229
TBA950:2X
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Tamb = +25°C
fo = 15625Hz in the test circuit Fig.2 (see note 1)
Characteristic
Symbol
Amplitude of frame pulse
Frame pulse duration
Output resistance at pin 7 (high state)
Amplitude of sync. pulse
Output resistance at pin 6
Output pulse duration
Residual output voltage
Oscillator frequency
VI
t7
Frequency pull-in range
Frequency holding range
Slope of phase comparator control loop
Gain of phase control
Phase shift between leading edge of
composite video signal and line flyback
pulse (see note 2) adjustable by VII
±t.fF
± t.fH
dfo/dtd
dtd/dt p
RouI7
Value
Min.
7.5
V6
RouI6
12
V2 res
fo
tv
2.5
25
14843
Typ.
Max.
>8
>150
10
13
>8
4.5
28.5
<0.55
15625 16406
400
400
V
J.1S
kO
V
kO
f1S
V
Hz
1000
1000
Hz
Hz
kHz/Jls
3.5
J.1s
2
20
-1
Units
Conditions
Typical range
12 = 20mA
C13/1 = 10nF
RU/l = 10.5k 0
Typical range
Typical range
T.YRical range
NOTES
1. By modification of the frequency-determining network at pins 13 and 14, these les can also be used for other line frequencies.
2. The limited flyback pulse should overlap the video signal sync. pulse on both edges.
OPERATING NOTES
The sync. separator separates the synchronizing
pulses from the composite video signal. The noise
inverter circuit, which needs no external components,
in connection with an integrating and differentiating
network frees the synchronizing signal from distortion
and noise.
The frame sync. pulse is obtained by multiple
integration and limitation of the synchronizing signal,
and is available at pin 7. The RC network hitherto
required between sync. separator and frame oscillator
is no longer needed. Since the frame sync. pulse
duration at pin 7 is subject to production spreads it is
recommended to use the leading edge of this pulse for
triggering.
The frequency of the line oscillator is determined by a
10 nF polystyrene capacitor at pin 13 which is charged
and discharged periodically by two internal current
sources: The external resistor at pin 14 defines the
charging current and consequently in conjunction with
the oscillator capacitor the line frequency.
The phase comparator compares the sawtooth
voltage, of the oscillator with the line sync. pulses.
Simultaneously an AFC voltage is generated which
influences the oscillator frequency. A frequency range
limiter restricts the frequency holding range.
The oscillator sawtooth voltage, which is in a fixed
ratio to the line sync. pulses, is compared with the
flyback pulse in'the phase control circuit, in this way
compensating all drift of delay times in driver and line
output stage. The correct phase position and hence the
horizontal position of the picture can be adjusted by
the 10k 0 potentiometer connected to pin 11. Within
the adjustable range the output pulse duration (pin 2)
is constant. Any larger displacements of the picture, e.g.
due to non-symmetrical picture tube, should not be
corrected by the phase potentiometer, since in all cases
the flyback pulse must overlap the sync. pulse on both
edges (see Fig. 3).
The switching stage has an auxiliary function. When
the two signals supplied by the sync. separator and the
phase control 'circuit respectively are in synchronism a
saturated transistor is in parallel with the integrated 2 k 0
resistor at pin. 9. Thus the time constant of the filter
230
Fig, 3 Phase relationships
network at pin 4 increases and consequently reduces
the pull-in range of the phase comparator circuit for the
synchronized state to approximately 50Hz. This
arrangement ensures disturbance-free operation.
For video recording operation this automaic switchover can be blocked by a positive current fed into pin 8,
e.g. via a resistor connected to pin 3. It may also be
useful to connect a rsistor of about 630 0 or 1 k 0
between pin 9 and earth. The capacitor at pin 4 may be
lowered, e.g. to 0.1 J.1F. These alterations do not
significantly influence the normal operation of the IC
and thus do not need to be switched.
The output stage delivers at pin 2 output pulses of
duration and polarity suitable for driving the line driver
stage. If the supply voltage goes down (e.g. by
switching off the mains) a built-in protection circuit
ensures defined line frequency pulses down to V3 = 4V
and shuts off when V3 falls below 4V, thus preventing
pulses of undefined duration and frequency. Conversely,
if the supply voltage rises, pulses defined in duration
and frequency will appear at the output pin as soon as
V3 reaches 4.5V, In the range between V3 = 4.5V and
full supply the shape and frequency of the output
pulses are practically constant.
TBA950:2X
RECOMMENDED OPERATING
CONDITIONS
For operating circuits Figs. 4 and 5
Input current during sync. pulse 15
> 5J.'A
Composite video input signal V;n p.p
3(1 to 6)V
Input current during line flyback pulse 110 0.2 to 2 mA
Switchover current 18
> 2mA
Time difference between the output pulse at pin 2
and the line, fJyback pulse at 10, td
< 20J.'s
Current consumption (see Fig. 6) i3
<31 mA
Ambient operating temperature range, Tamb 0 to +60 0
~IDEompUT
SIGNAL 'lIN
Fig. 4 Operating circuit (thryistol OiJtput stage) *Input circuitry must be optimised
c-------------+---------~--_,rC==J-~--~-----~c
r: '
I[
VIDEO INPUT
SIGNAL 'In>!
Fig. 5 Another possiblity for line frequency adjustment (transistor output stage) 'Input circuitry must be optimised
231
TBA950:2X
'"
,
"' ,
'"
00
All voltages are referred to pin 1
Supply current (see Fig. 6) Is:
45mA
Input current Is:
2mA
-6V
Input voltage Vs
Output currenJ 12
22mA
Output voltage V2 :
12V
Switch-over current for video recording Is
5mA
Phase correction voltage V" :
to V3
Operating temperature range -10°C to +60°C
-55°C to + 125°C
Storage temperature range
"AXI I
I VMIN
~ 30
20 0
ABSOLUTE MAXIMUM RATINGS
I
II I
J
o
I II
II
'I
20
"
Fig. 6 Graph for determining the supply series resistor R5
232
.I!!!e!
CONSUMER
TV CIRCUIT
TCA800
COLOUR DEMODULATOR WITH FEEDBACK ClAMPS
A monolithic integrated circuit for colour television
receivers
incorporating
two
active
synchronous
demodulators for the FS_y and ±FR_y signals, a G-Y
matrix, PAL switch bistable and RGB matrix, suitable for
driving simple single transistor video output stages_ The
circuit incorporates three feedback clamps to stabilise the
black level, to eliminate the problem of thermal drift in the
demodulators.
LUMINANCE liP
1
EARTH
DECOUPUNG
1
R_Y REFERENCE
REO OfP
3
DECOUPLING
~
GREEN DIP
5
UNE PULSE liP
For alternative applications in a simple decoder circuit,
it must be possible to trigger the flip-flop so that it runs in
the correct ident. phase by means of an AC coupled, 2 volt
pop square wave, derived from the APC loop in the
reference generator circuit. (The normal input line timebase
pulse would still be applied in order to provide clamp
pulses.)
Input impedance of output amplifier (BF337)
(Expressed as parallel resistance and capacitance.)
R (typ_) 5kU
C (typ.) BOpF
The above values are given for suitable design of output
stages i.e. emitter follower with 5mA current capability.
Hf2 DIP
"
R-YCHAOMAlfP
Of COUPLING
10
BLUE DIP
OPERATING NOTES
lDENT liP
8-V REFERENCE
TCA
B••
"1,;...._--t'
8-Y CHROMA liP
Vee
OP16
Fig. 1 Pin connections
QUICK REFERENCE DATA
Vsupply -(Nominal) 12V
IsuPPly -(Nominal) (Is = O.5mA) 47mA
Voltage Gain of Chrominance (R-Y) Signal
Channel (typ.) Vin(p-p) = 50mV; f
4.43MHz; Video Gain = X20 17.5V/V
Voltage Gain of Luminance (Y) Channel Vin
(Black-ta-White) = 1V (p-p) 5V/V
Operating Temperature Range -10 to +55°C
~-------------------------------~
,,
h,,
'",
,,
!
,,'
Fig. 2
Block diagram and typical application circuit
233
TCA800
ELECTRICAL CHARACTERISTICS
Test Conditions (unle .. otherwise stated):
Tamb = +2SoC, Vee = +12V
Value
Characteristic
Pin
Conditions
Units
Min, Typ, Max.
Supply voltage range
9
10.8
Voltage gain of chrorninance (R· Y)
signal channel
12
13.2
V
17.S
VIV
V in p.p = SOmV, f = 4.43MHz,
video gain = X20
V in (black.to.white) = lV p.p
Voltage gain of luminance (Y) channels
Bandwidth (-3dB) of luminance channel
from Y input to R·G·B outputs
5
VIV
10
MHz
Bandwidth (-3dB) of chroma channel from
F(R.Y), FIB.Y) inputs to R·G·B outputs
1
MHz
Ratio of demodulated signals
V(B·y)IVIR·Y)
VIG·y)IV(R.Y)
1.60 1.78 1.96
0.76 0.85 0.94
I nput Characteristics
Chrominance input impedance (expressed
as resistance and parallel capacitance
10,11
R
C
I
1000
Defined with equal chroma input signals
and measured at output pins (see note 1)
10
n
pF
1.8
V
Luminance (Y) input blanking level
(fixed by TBA560)
1
Luminance (Y) input, black level
potential (nominal brightness set by
brightness control of TBA560)
1
1.7
V
Luminance (Y) input black·to·white
amplitude (adjusted by contrast
control of TBA560)
1
1.0
Vp·p
Reference input impedance (expressed
as resistance and parallel capacitance)
R
C
1.4
1.5
f
= 4.43MHz, V in = 20mV sinewave
f
= 4.43MHz
13,15
5.0
5.0
10
kn
pF
2.0
V p.p
Reference input voltage
(from TBA540)
13,15 0.5
1.0
Phase shift between reference inputs
and chroma input signal to give
coincidence at the synchronous
demodulators
13,15
10
degrees
Ident. voltage for ident 'off
14
Ident. voltage for ident 'on'
14
+7.0
V
Ident. current for ident 'off'
14
0.1
rnA
0.6
mA
1.4
k!1
+6
V
Tracking of ident. threshold with a
supply variation of ±10%
f>Vthre,hold . Vee
VthreShold . f>Vee
14
Required line pulse input current to
clamps and H/2 flip·flop
8
Window level (see note 2)
8
Line input impedance
8
Output Characteristics
R·G·B outputs blanking level
234
0.3
0.45
+12.!
0.6
1.0
V
2.0
3,S 7
Common mode variation of black level
va. iation over a temperature range
of 40°C
Blanking·to·white level output
voltage capability of each output
amplifier channel
1.0
VDC Blanking level at pin 1 = 1.5V
See note 3
3. 5, 7
6
8
V p.p
TCA800
,
Value
Characteristic
Conditions
Units
Pin
Min. Typ. Max.
Difference in clamped blanking
level of outputs i.e., R to G to B
3,5,7
50
mV
Differential drift of clamped output
blanking levels over temperature
range of 40° C
3,5,7
25
mV
Residual 4.43MHz signal at R·G·B
outputs
Red
Blue
H/2 square wave output amplitude
150 mV pop
300 mV p.p
12
2.5
3.5
V p.p Measured with 3kn load i.e. TBA540
NOTES
1. These values are chosen to minimise errors in flesh tones and of the luminance of the green component. The matrix equation for the
derivation of the G-Y component is given by G· Y = -0.51 (R·Y) -O.19(8·YI, (This is derived from the basic colour equation Y '" O.30R +
O.59G +0.11 B.) Measured at the tube cathodes with 100V pop video drive.
2.
In order to provide a clamp pulse which occurs inside the blanking waveform and free from the edge spikes, it is necessary to window the
line pulse at about two thirds of its amplitude.
3.
In order to partially compensate for drift in output stages a negative temperature coefficient to compensate for the variation in the video
output transistor has been incorporated.
-------.'"
~
, ----------125'"
'
, ,
,I
~
,,
LINE PULSE
,I
i : r--- aLAN~ING
"':
JlL
~
I
1
I
,
,
3" • ....:
:
~
@
+55°C = 900mW
Storage temperature range -55°C to
+ 125°C
WAVEFORM
FROM TaA5~O
I
'
I
t
ABSOLUTE MAXIMUM RATING
Max. dissipation
CLAMP PULSE
~3"s
Fig. 3 Line pulso, blanking and clamp timings
235
236
CONSUMER
TV CIRCUIT
TDA440
VIDEO IF AMPUFIER/ DEMODULATOR
The TDA440 incorporates the following functions:
1.
Three-stage symmetrical IF (broad band) amplifier
with first and second stages AGC-controlled.
Controlled video carrier demodulator.
2.
Video drive amplifier whh low-pass response and
3.
output independent of supply fluctuations.
Gated AGC section for I F amplifier.
4.
Delayed regulated output voltage for the tuner
5.
preamplifier.
IF liP (DIFFERENTIALI
1
DECOUPlIN(J
2
OV
J
CONTROL VOLTAGE
DECOUPLING
TUNER AGe
-
TOA41.0
DEMODULAtOR TUNING
IF I/PIDIFFERENIIALI
IS
DEcnuPLING
1~
5 r AHILISER liP
1]
Vee
12
:}
10
WHilE LEVEI.PRESEl
s
TUNER AGe THRESHOLD
CONTROL
GATING PULSE lIP
16
'1
VIDEOQ/P,
'i;.'_ _......;'.t' DEMODULATOR lUNING
OP16
Fig. 1 Pin connections.
FEATURES
•
•
High Gain - High Stability
Constant Input Impedance Independent of
•
•
..
..
..
AGC
Low Noise Independent of AGC
High Supply Rejection
Low RF Breakthrough to Video O/Ps
Fast AGC Action
1'1
..
..
•
..
..
I~~-~:
Very Low I ntermodulation Products
Minimum Differential Error
Positive and Negative Video O/Ps
Low I mpedance Video O/Ps
Temperature Compensated
Peak White Adjustable
VIOEO
OUTPUTS
'w
~
I
1'5 r---'F'="AMPLiF'ER----1
=8!
rlIH~I''''+-''
I
'--f--¥+IA"
'--- ------~;~-I'
I
I
I
I
I
T~-J
GATING PULSE
Fig. 2 TDA440 block diagram.
237
TDA440
ABSOLUTE MAXIMUM RATINGS
Reference point is pin 3
Rating
Supply voltage range
Low voltage stabiliser supply current
Open loop voltage
Video DC output current
Average positive
Peak positive
Average negative
Peak negative
White level control
Power dissipation at Tam b ';;55° C
Ambient temperature range
Storage temperature range
Pin
Symbol
Value
Units
13
14
5
Vee
10 to 15
50
15
V
mA
V
12
12
1'2
1'2
5
30
5
30
3.2
700
-10 to +65
-55 to +125
mA
mA
mA
mA
V
mW
I,
Vs
)1
I"
I"
l'
10
Vl0
Ptot
Tamb
T'lg
°c
°c
VIDEO
OUTPuts
~
Vee
]8-9
MH,
lUNER
GAltN" PULSE
Supply voltage must be disconnected before inserting the integrated circuit into the test socket.
Fig. 3 Test and application circuit.
C=
38·g
MH,
Parasitic capacitance at pins 8 and 9 should be kept to
a minimum.
6 to 1OpF series capacitance.
Series resonant frequency = 38.9 - 11.8102.75) MHz.
Series
resonance
damping
(determines
tuning
characteristics) = 1.B to 3.3kU E.G•• with Rs
2.4kn. tuning range. f, = 3MHz.
Fig. 4 Modifications to Fig. 3 for improving audio interference and/cfOSI"Colour characteristics.
238
=
TDA440
ELECTRICAL CHARACTE R ISTICS
Test Conditions (unless otherwise stated):
T&mb;+25°C
Vee ;+12V
Reference point is pin 3
Value
Characteristic
Supply voltage, Vee
Supply current, 1'3
Supply voltage, stabiliser input
Positive video DC output voltage
White level adjustment range
for positive video DC output voltage
Pin
13
13
14
11
Typ.
Max.
10
15
5.5
12
19
5.B
5.5
15
25
6.4
V
mA
V
V
4.B
V
V
1.9
3.2
5.6
7.5
3
3.3
4.2
56
10
1.0
2.15
V
mA
V
mA
Vp·p
Vp-p
Vp-p
dB
MHz
dB
150
220 IlVr.m.s
11
11
12
5
7
11
AGC range, L'lAGC
Video 3dB bandwidth
Video frequency response change
1.75
7
1.5
50
B
Symmetrical input voltage for
3.3Vp-p output (pin 11)
Maximum IF voltage level present
at video outputs over the full
AGC range
11,12
Sound IF voltage level present at
video outputs with selective circuit
12
1-16 100
Differential gain of negative
compo video output signal for
full black to white swing
Suppression of sound carrier/colour
subcarrier (1.07MHz) w.r.t
colour subcarrier level
Input impedance
AGC max.
AGCmin.
1,4; 40mA
11
6.5
Peak black clamping level for
positive video DC output voltage
DC output current
Negative video DC output voltage
Available tuner control current
Negative gating pulse
Composite video output level
Conditions
Units
Min.
5
2.0
30
50
30
15
40
Reference point pin 13
1OdB after onset of tuner control action
V1 1 ; 5.5VDC
V11 ; 6.4VDC
L'lAGC ; 50dB, video bandwidth; 0 to 5
MHz
mV
mV
f; 38.9MHz
f; 77.BMHz (2nd harmonic)
mV
f; 5.5MHz, picture carrier level
sound carrier level
30dB
%
dB
1
1.4112
1.4#1.9
Rw (pin 10); co
Rw (pin 10) ; 0
Picture carrier; OdB, IF colour subcarrier
level; -6dB, IF sound carrier level;
-24dB
Reference point pin 16
kW'pF
kl1/,1pF
239
240
CONSUMER
lVCIRCUITS
TDA2522/3
COLOUR DEMODULATOR COMBINATION
The TDA2522 and TDA2523 are integrated synchronous demodulators for colour television receivers.
The devices incorporate an 8.8M Hz oscillator followed
by a divider giving two 4.4M Hz reference signals, a
keyed burst phase detector for optimum noise behaviour, an ACC detector and amplifier, a colour killer,
two synchronous demodulators for the (B-Y) and
(R-Y) signals, a PAL switch and a PAL flip-flop with
internal identification.
The symmetrical demodulators include integrated
capacitors to reduce unwanted carrier signals at the
outputs which are taken from temperature-compensated
emitter followers. The outputs of the TDA2522 are
suitable for use with the TDA2530. The TDA2523
outputs are inverted for use with a direct transistor
drive..
COLOUR
DIFFERENCE
OUTPUTS
liB -V)
[
,
.p KIllER DELAY CAPACITOR
(G-YI [ 1
,,~ BUAST GATING AND BLANKING PULSE I/P
.IR-Y
l
"p Ace HOLD CAPACITOR
GROUND
4
"
lIR-V
,
REF.QSCllLATIlR f
CHROMJNANC[ JIB-V)
INPUTS
6
AfCHlTER
l
8
"p
Ace QUTPUT
"b Ace REFERENCE VlllTAGE
"p , lZV
'" tf
9
OSCILLATOR
CRYSTAL
DP16
Fig. 1 Pin connections
QUICK REFERENCE DATA
Ell Supply Voltage (pin 11):
12V typo
II Supply Current:
40mA typo
II Colour Difference Signals:
(R -Y) (pin 3) :
> 2.4V P:-P
(G -Y) (pin 2) :
> 1.35V p-p
(B-Y) (pin1):
>3Vp-p
III Chrominance Input Signal (Including
Burst) :
R -Y (pin 6)
500mV p-p
B -Y (pin 5)
350mV p-p
II Colour Difference Signal Output
Impedance 250..IL. typo
[6-YI
Fig.2 Block diagram
241
TDA2522/TDA2523
ELECTRICAL CHARACTERISTICS
Test conditions unless (otherwise stated):
Supply voltage, pin 11 = + 12V
Tamb = +25°C
Measurements referred to pin 4
Charateristic
Demodulator
Ratio of demodulated
signals:
B-Y/R-Y
G-Y/R-Y
G-Y/R-Y
Colour difference outputs:
(R-Y)
(G-Y)
(B-Y)
Chrominance input signal
(inCluding burst) :
R-Y
B-Y
Colour difference signal
output impedances:
(R-Y)
(G-Y)
(B-Y)
H/2 ripple at R -Y O/P
Blanking and keying pulse:
Burst keying active for
Burst keying inactive for
Blanking active for
Blanking inactive for
Reference section
Phase difference between
reference and burst
Pin
Value
Min, Typ.
1/3
2/3
2/3
1.78
0.85
0.17
3
2
1
-
See note 1
See note 2
Vp-p
Vp-p
\lp-p
500
350
3
2
1
3
250
250
250
Overall holding range
Burst signal input
5-6
Oscillator input resistance 10
Oscillator input capacitance
10
Oscillator output resistance 9
ACC reference voltage
12
ACC voltage at correct
phase
14
ACC voltage with zero
burst
14
ACC amplifier output
voltage range
13
Colour killer
Via pin 14:
Colour off
14
Colour on
14
Via pin 16:
Colour off
16
Colour on
16
Colour unkill delay
Conditions
-
2.4
1.35
3
6
5
15
15
15
15
Units
Max.
i mVp _p
mVp-p
,
10
7.5
6.5
2
1
} See note 3
Q
Q
Q
mVp-p
Vp-p
Vp-p
Vp-p
Vp-p
Oeg.
±5
±500
0.25
270
Q
200
7
V
5.5
V
7.0
V
Crystal frequency deviation
±400Hz
Using typical crystal
Keying pulse width = 41ls.
Hz
Vp-p
pF
0.5
5.0
V
5.6
V
V
6
7
5
20
See note 5
Q
V
V
mS/IlF
~
Burst = 0.25Vp-p
113 < ±2001lA
See note 6
NOTES
1. The demodulators are driven by a chrominance signal of equal amplitude for the (R-Y) and (B-Y) components. The phase of the
(R-Y) chrominance signal equals the phase of the (R-Y) reference signal. The same holds for the (B-Y) signals.
2.
3.
4.
5.
6.
As note 1. but with the phase of the (R-Y) reference signal reversed.
Colour bar with 75% saturation.
The burst amplitude IS kept constant by ACC action. but depends linearly on the keying pulse width.
To be established.
The delay depends on the value of Cd (see Fig. 2)
242
TDA2522/TDA2523
FUNCTIONAL DESCRIPTION
Functions listed by pin number.
TDA2522
TDA2523
1. -(B-Y) signal output
(B-Y) signal output
2. - (G- Y) signal output
(G-Y) signal output
3. - (R-V) signal output
(R-Y) signal output
These outputs are of low impedance from temperature compensated emitter follower stages that require
external loads of 10kO. Internal filtering of the colour
difference output signals to give a -3dB bandwidth of
1 MHz allows the three signals to be fed directly to the
luminance matrix. The TDA2522 may be AC coupled to
the TDA2530, and the TDA2523 may be used with
direct transistor drive.
4. Negative supply (Ground)
5. Chrominance B -Y input signal
An input signal of approximately 350mV p-p (colour
bars) is required at this pin. The B - Y component of
colour burst must be included with the input chrominance signal.
6. Chrominance R -v input signal
An input signal of approximately 500mV p-p (colour
bars) is required, including the R -Y colour burst
component.
7. Reference oscillator APC loop filter
8. Reference oscillator APC loop filter
Between pins 7 and 8 are connected the APC loop
low pass filter components. The difference voltage
between these pins is connected internally to the
oscillator reactance stage.
9. Oscillator feedback
10. Oscillator feedback
A series network consisting of the 8.8M Hz crystal
and an adjustable tuning capacitor is connected
between pins 9 and 10. Division from the 8.8M Hz
oscillator within the I C produces the4.4M Hz quadrature
reference carriers which are then applied to the
colour demodulators.
11. Positive 12V supply
The maximum voltage must not exceed 14V.
12. ACC hold capacitor
The capacitor connected from this pin to ground is
normally charged to a potential of about 7V.
13. ACC output potential
An output potential varying inversely with the input
colour burst amplitude is available at pin 13. Maximum
ACC gain of the TDA2560 is provided when the ACC
potential from pin 13 of the device is greater than
about 1.4V.
14. ACC hold capacitor
The capacitor connected from this pin to ground is
normally charged to a potential of 5.5V. On monochrome reception the potential will be 7.0V and while
identing it may instantaneously increase to about 8V.
A 1000 resistor may be connected in series with the
capacitor from pin 14, see pin 15.
15. Burst gating and blanking pulse input.
The two-level positive pulse required at this pin is
used for burst gating and flip-flop triggering. at a
sampled level of 7V. A negative going pulse of about
100mV p-p, derived from the colour burst, may be
inspected across a 1000 resistor in series with the
capacitor from pin 14 to ground, should the sandcastle
pulse shape require some adjustment. At a level of about
1.5V the pulse width should be suitable for chroma
blanking.
16. Killer delay capacitor
The value of a capacitor connected from pin 16 to
ground determines the delay of un-killing. By this
means the state of continuous switching of the killer
with marginal signals. may be avoided. Connecting pin
16 to ground unkills the system.
ABSOLUTE MAXIMUM RATINGS
Supply voltage (pin 1)
14V
Total power dissipation
600mW
Storage temperature
-55°C to + 125°C
Operating ambient temperature -10°C to +60°C
243
244
CONSUMER
lVCIRCUITS
TDA2530/2
RGB Matrix Preamplifier (with clamps)
The TDA2530 and TDA2532 are integrated RG B
matrix preamplifiers for colour television receivers,
incorporating a matrix preamplifier (for RG B cathode
drive of the picture tube) with clamping circuits.
This integrated circuit has been designed to be
driven from the TDA2522 synchronous demodulator
and oscillator IC.
The TDA2532 has been designed for use with onscreen data display systems.
LUMINANCE INPUT
-!R~YI
INPUT
RED DRIVE ADJUSTMENT
-IG-Y) INPUT
--..r-,
II; ~ GAOUND
,
,
"
-18-'1IINpUr
ClAMP PULSE INPUT
QUICK REFERENCE DATA
P
PGRHN SIGNAL DUTPUT
II PBLUE SIGNAl fHoilACX
p' BLUE SIGNAl OUTpuT
9 PPOSITIVE SUPPLY
U GREEN SIGNAl fEEDBACK
1]
GREEN DRIVE ADJUSTMENT
8lUJA~~~~~~~~ri m~~
REO SIGNAL FEEDBACK
'" bRm
SltmAL OUTPUT
14
"
I
•
\(1
DP16
Fig. 1 Pin connections (top view)
II Supply Voltage (pin 9): 12V typo
II Operating Ambient Temperature Range:
-10 to +60·C
II Luminance Input Resistance (pin 1) :
100kn min
II Colour Difference Input Currents
(pins 2, 4 & 6):
Unclamped
2 flA typo
During Clamping
-0.2 to +0.2mA
.. Clamping Pulse Input Current (pin 8) :
20flA max.
'.A~D(AS
HE OR HORIZONTAl
lUMI .. Al-lCE IYI
II
Gain of RGB Preamplifiers:
OdB typo
.. Gain DC Adjustment Range:
±3dB typo
II Error Amplifier Gain (Conductance):
20mAN typo
II Feedback Input Currents (pins 11, 13 &
15):
2 flA typo
II Output Current Swing (pin!; 10, 12 & 14):
-4.4 to +4.4mA
DATA.
BLANKING
J.'l;lSf
+__;±;~;~~~==I=~__~~~~~~~~~~~;;~--<~_fHDBA(K
GFHfN SIGNAL
- G-1I-I
1-
•
a-GAIN PRESfT
TO OUTPIJI
TRANSl5TOR
(BLUE)
BLUE
SIGNAL
FEEDBACK
"-l~'l--L---=:r----------'
t
TOA
* TOA
2~30
2~n
OhlY
Ohl'
Fig. 2 TDA2530/2 block diagram
245
TDA25301 TDA2532
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated):
Supply voltage (pin 9) = + 12V
Luminance input (pin 1) = 1.5V
Tamb = +25°C
Measurements refer to pin 16
Test circuit Fig. 3
Characteristic
Current consumption
Luminance input
Black level
Black-to-white input voltage
Input resistance
Colour Difference Input
Input signals
-(R-Y)
-(G-Y)
-(B-Y)
Input currents
Input currents during clamping
Clamp Pulse Input for DC Feedback
Clamping voltage
ON
OFF
Clamping current
ON
OFF
Feedback Input
DC level during clamping
Gain Adjustment for Colour Drive
Adjustment voltage range
Adjustment voltage for nominal gain
Nominal gain between colour difference
inputs, luminance input and colour
feedback inputs
Adjustment range of nominal gain
Differential Amplifier
Feedback input current
Error amplifier gain
Output current swing
Integrated load resistance
Output bias voltage
Data blanking (TDA2532 only)
Pin
Value
Units
Min. Typ. Max.
9
50
mA
1.5
1.0
V
Vp-p
kO
1.4
0.82
1.78
2
Vp-p
Vp-p
Vp-p
Conditions
1
100
2
4
6
2,4,6
2,4,6
8
4
~
See Note 1
~A
mA
±0.2
7.5
0
12
5.5
V
V
1
20
~A
~A
} See Note 2
11, 13, 15
0.5Vs
3,5,7
3,5,7
3,5,7
11, 13, 15
10,12,14
10,12,14
10,12,14
7
10
0
1-1, 13, 15
V
5
V
V
0
dB
dB
±3
2
20
' 4.4
680
8
~1
} See Note 4
At=!1V3,5,7, =±5V
~A
mAN
mA
0
V
V
See Note 3
See Note 3 and
applications
information
Pins 10, 12, 14
go to +6V
NOTES
1. The allocation of -(R-Y), -(G-Y) and -(B-Y) srgnals to pins 2. 4 and 6 respectively, is not mandatory as all three channels are
identical.
2. SWitching from clumping ON to OFF occurs at about 6V.
3. The Integrated load reSistors Include series diodes. this means that the resistors can be ignored when V10. V12. V14 > V9. Under this
conditIOn, external load resIstors must be chosen such that the current IS nominally 4.4mA. See Fig.3.
4. The TDA2532 uses pin 7 for data blanking. the gain of one channel is therefore internally preset.
APPLICATIONS INFORMATION
(fig 3)
The clamping level, Vel of the video output stages,
with set clamping level potentiometers in their midpositions, is given by:
R1
R1
Vel = V9 (1 + R'2-"R3)
The gain of the video output stages is given by:
Gain ··c 1 + R1 + Rl + Rl
R2
R3
R4
246
Attention should be given to earth paths, avoiding
common impedances between the input (decoder) side
and the output stages.
Printed track area connected to the feedback pins
should be kept to a minimum.
To ensure a matched performance of the video output stages, a symmetrical layout of three stages should
be employed.
TDA2530/TDA2532
1601/
S,ANO(A';lLf PUlS€
140V
f\.
or NROH TOA
2~91J 1
L-----j---===:::=====j:-t-<>
".
BLU[
BA" 21
1---------1-----+---0 ",0
,
>0.
FIGS GAIN
PRESETS
1~5
TO 1401
DAtA
DATA
~
TOA lSH ONLY
Fig. 3 TDA2530j2 applications and test circuit
FUNCTIONAL DESCRIPTION
Functions listed by pin number
1. Luminance signal input.
A 1 V black to white positive going luminance input
signal is required. Blanking level should be at 1 .5V and
black level at 1 .7V
2. -(R -V) input signal
The input signal is required to be AC coupled from a
low impedance source such as the TDA2522. The
coupling capacitor also acts as a clamp capacitor for the
TDA2530/2 red output. As the colour difference input
impedance is at least 100kQ. low value coupling
capacitors may be used.
3. Red drive adjustment.
A gain variation of the red channel of at least ±3dB
about the nominal. is obtained as the DC potential at
this pin varies by :1 5V about the nominal of 5V. If no
connection is made to a gain controlling pin the channel
concerned assumes the nominal gain.
4. -(G -V) input signal (see pin 2)
5. Green drive adjustment (see pin 3)
6. -(B -V) input signal (see pin 2)
7. TDA2530: Blue drive adjustment (see pin 3)
TDA2532: Data blanking input.
When this pin' is taken above 1 V the colour output
signals on pins 10. 12 and 14 are inhibited. the outputs
being clamped to 6V.
8. Clamp pulse input
A positive going line pulse input is required and the
pulse should exceed a threshold DC level set by the
TDA2530/2 of 7.5 V. An input current of about 0.2mA
is required. A maximum current of 1 mA should not
be exceeded.
9. Positive 12V supply.
10. Blue signal output
11. Blue signal feedback
The signal gain of both the video output stages and
I C amplifier are stabilised by the feedback circuits. DC
clamping is achieved by sampling of the feedback level
during blanking. The black level potentials at the
collectors of the video output stages may be varied
independently by adjustable DC current sources applied
to the feedback input pins. The DC levels at these pins
are such that the feedback resistor and a resistor network between the 12V supply and earth provide a
potential of 6V during blanking.
12. Green signal output
13. Green signal feedback (see pin 11)
14. Red signal output
15. Red signal feedback (see pin 11)
16. Negative supply (earth)
ABSOLUTE MAXIMUM RATINGS
Voltages
Supply voltage (V9)
15V
Pin 1. 2. 3. 4. 5. 6 & 7
OV to V9
Pin 8
V9
Pin 10
V9 to V9 + 3V
Pin 12
V13tOV9 + 3V
Pin 14
V15tOV9 +3V
Pins 11. 13 and 15
0.3V9 to V9
Current
Pin 8
1mA
Thermal
Total power dissipation
1W
Storage temperature
-55°C to + 125°C
Operating ambient temperature -10°Cto +60°C
247
248
•
CONSUMER
PLESSEY
Semiconductors
lVCIRCUITS
TDA2540 TDA2541
TELEVISION IF AMPLIFER AND DEMODULATOR
(TDA2540 for NPN tuners, TDA2541 for PNP tuners)
The TDA2540 and TDA2541 are IF amplifier and
demodulator circuits for colour 811d monochrome
television receivers using NPN and PNP tuners
respectively. The two circuits are in other respects
identical. A VCR switch is incorporated for switching
off the video signal when inserting a VC R playback
signal.
If INPUT
[~PlfINPUT
O£COUPUNG [ /
1~
PVCR SWITCH
TUNER AGe OUTPUT [ 4
u
GRDtJ~O
Afe OUTPUT [ "
"
AFC SWITCH [ Ii
FEATURES
•
•
•
•
•
•
•
•
Gain-Controlled Wideband Amplifier.
Providing Complete I F Gain
Synchronous Demodulator
White Spot Inverter
Video Preamplifier with Noise Protection
DC Controlled AFC
AGC Circuit with Noise Gating
Tuner AGC Output
VCR Switch
"
VIDEO OUTPUT
POSITIVE SUPPLY
AFt TUNING [ I
20dB
Saturation Control Range
>20dB
to
~T~(
~IPAUIO~
'"
CONTRAST CONTROL
"
OUTPUT TO SYNC SEPARATOR
.,
"
"
LUMINANCE INPUT
,
"PBLACK LEVEL CLAMP CAPACITOR
11
BRIGHTNfSS CONTRDt
I
lU
bLUMmANCE OUTPUT
B
9
PBLANKING PULSE INPUT
3
LUMINANCE GAIN CONTROL
DP16
Fig. 1 Pm connectIons (top View)
FEATURES
Luminance Amplifier
DC Contrast Control
DC Brightness Control
Black Level Clamp
Blanking
Additional Video OIP with +ve Sync.
••
•••
••
•
•
Chrominance Amplifier
Gain Control Amplifier
Chrominance Gain Control Tracked with
Contrast Control
Separate DC Saturation and Contrast
Controls
Direct Delay Line Drive
lU~I~UCI
CII,ITPUI
Fig. 2 TDA2560 block diagram
253
TDA2560
ELECTRICAL CHARACTERISTICS
Test Conditions (unless otherwise stated):
Supply voltage (pin 8) = + 12V
T,mb= +25°C
Gain setting resistor, RG, (pin 13) = 2.7kO
Measurements referred to pin 5
Test circuit Fig. 5
Vall!e
Characteristic
Units
Pin
Min.
Supply voltage range
Supply cyrrent
8
8
Permitted supply line hum
Luminance Amplifier
Input signal current
Input bias 'current
Input impedance
Gain
Contrast control range
Contrast control voltage range
Contrast control current
Black level range
Typical brightness control
voltage range
Brightness control current
Black level temperature
stability
Black level stability when
changing contrast
8
12
45
14
V
mA
100
mAp-p
mA
mA
0
11
11
Load on pin 6 = 1.5kO
no load on pins 10 and 15
Black-to-white value
Input bias current = 0.25mA
See operating Note 1
dB
20
16
16
10
Conditions
Max.
0.2
0.25
150
14
14
14
13
See Fig. 3
8
3
1
1
3
20
V
V
~A
MHz
5
V
Vp-p
3
3.4
10
15
7
~A
7
Va
5
2.5
4.5
1.5
Va
4.5
See functional description
(pin 10)
At nominal contrast (Max
contrast setting -3dB)
Black-to-white value
114 = 0.2mA black-to-white
See Operating Note 2
V
V
9
6
V,,>4V
mV;oC
0.1
Bandwidth (-3dB)
Output voltage
Output to sync separator
Black level clamp pulse
ON
OFF
Blanking pulse
ON
OFF
ON
OFF
Chrominance Amplifier
Input signal
Chrominance output signal
at nominal contrast and
saturation level
Max, chrominance output
Bandwidth (-3dB)
Ratio of burst and
chrominance at nominal
contrast and saturation
ACC starting voltage
ACC range
Tracking between luminance
and chrominance with
contrast control
Saturation control range
Saturation control voltage
range
Gating pulse
ON
OFF
Width
Signal-to-noise ratio
Phase shift between burst
and chrominance
10
Typ.
See Operating Note 3
For OV on pin 10
V
V
V
·For 1.5V on pin 10
See note 1
2-1
80
4
6
6
3
mVp-p
2
4.6
6
Vp-p
V
MHz
1.2
V
dB
30
dB
dB
±1
20
4
See note 2
See Operating Notes 4 and 5
See Operating Note 6
10dB control
See Fig. 4
7
2.3
5
1
V
V
ps
dB
5
deg
8
46
NOTES:
1. A!I'figures for the chrominance signals are based on a colour bar signal with 75 per cent saturation: i.e. burst-to-chrominance ratio is 1 :2.
2. At a bur5t,signal of 1V peak-to-peak: see also Operating Notes 4 and 5.
254
TDA2560
0
0
(
/
II
I
II
/
II
0
0
I
I
II
I
/
0
1-
..J
2
V,-s IV)
V 16 - 5 (V)
Fig. 4 Saturation control of chrominance amplifier
Fig. 3 Contrast control of luminance and chrominance amplifier
Functions listed by pin number.
1. and 2. Balanced chrominance input signal
This is derived from the chrominance signal bandpass
filter, designed to provide a push-pull input. A signal
amplitude of at least 4mV peak-to-peak is required
between pins 1 and 2. The chrominance amplifier is
stabilized by an external feedback loop from the output
(pin 6) to the input (pins 1 and 2). The required level
at pins 1 and 2 will be 3V.
3. ACC input
A negative-going potential, starting at + 1.2V, gives
a 40dB range of ACC. Maximum gain reduction is
achieved at an input voltage of 500mV.
4. Chrominance saturation control
A control range of +6dB to -14dB is provided
over a range of DC potential on pin 4 from +2 to +4V.
The saturation control is a linear function of the control
voltage.
5. Negative supply (ground)
6. Chrominance signal output
For nominal settings of saturation and contrast
controls (max. - 6dB for saturation, and max. -3dB
for contrast) both the chroma and burst are available at
this pin, and in the same ratio as at the input pins 1 and
2. The burst signal is not affected by the saturation and
contrast controls. The ACC circuit of the TDA2522 will
hold the colour burst amplitude constant at the input
of the TDA2522. As the PAL delay line is situated here
between the TDA2560 and TDA2522 there may be
some variation of the nominal 1 V peak-to-peak burst
output of the TDA2560, according to the tolerances
of the delay line. An external network is required from
pin 6 of the TDA2560 to provide DC negative feedback
in the chroma channel via pins 1 and 2.
7. Burst gating and clamping pulse input
A two-level pulse is required at this pin to be used
for burst gate and black level clamping. The black level
clamp is activated when the pulse level is greater than
7V. The timing of this interval shoLI1d be such that no
appreciable encroachment occurs into the sync pulse
on picture line periods during normal operation of the
receiver. The burst gate, which switches the gain of the
chroma amplifier to maximum, requires that the input
pulse at pin 7 should be sufficiently wide (at least
8~s) at the actuating level of 2.3V.
j
0
2
FUNCTIONAL DESCRIPTION
/
8. + 12V power supply
Correct operation occurs within the range 10 to 14V.
All signal and control levels have a linear dependency on
supply voltage but, in any given receiver design, this
may be restricted due to consideration of tracking
between the power supply variations and picture
contrast and chroma levels.
9. Flyback blanking input waveform
This pin is used for blanking the luminance amplifier.
the input pulse exceeds the +2.5V level, the
output signal is blanked to a level of about OV. When
the input exceeds a +6V level, a fixed level of about
1.5V is inserted in the output. This level can be used
for clamping purposes.
Wh~n
10. Luminance signal output
An emitter follower provides a low impedance output
signal of 3V black-to-white amplitude at nominal
contrast setting having a black level in the range 1 to
3V. An external emitter load resistor is not required.
The luminance amplitude available for nominal contrast may be modified according to the resistor value
from pin 13 to the + 12V supply. At an input bias
current 114 of O.25mA during black level the amplifier is
compensated so that no black level shift more than 10V
occurs at contrast control. When the input current
deviates from the quoted value the black level shift
amounts to 1 OOmV /mA.
11. Brightness control
The black level at the luminance output (pin 10)
Is identical to the control voltage required at this pin.
A range of black level from 1 to 3V may be obtained.
12. Black level clamp capacitor
13. Luminance gain setting resistor
The gain of the luminance amplifier may be adjusted
by selection of the resistor value from pin 13 to +12V.
Nominal luminance output amplitude is then 3V
black-to-white at pinl0 when this resistor is 2.7kQ and
the input .current is 0.2mA black-to-white. Maximum
and minimum values of this resistor are 3.9k Q and
1.8kQ.
14. Luminance signal input
A low input impedance in the form of a current sink
is obtained at this pin. Nominal input current is O.2mA
255
TDA2560
black-to-white. The luminance signal may be coupled
to pin 14 via a DC blocking capacitor and, in addition,
a resistor employed to give a DC current into pin 14
at black level of about· O.25mA. Alternatively DC
coupling from a signal source such as the TDA2541
may be employed.
15. luminance signal output for sync separator
purposes
A luminance signal output with positive-going sync
is available which is not affected by the contrast control
or the value of resistor at pin 13. This voltage is intended
for drive of sync separator circuits. The output amplitude
is 3.4V peak-to-peak when the luminance signal input
is O.2mA black-to-white.
16. Contrast control
With 3V on this pin the gain of the luminance channel
is such that O.2mA black-to-white at pin 14 gives a
luminance output on pin 10 of 3V black-to-white. The
nominal value of 2.7k 0 is then assumed for the resistor
from pin 13 to the + 12V supply. The variation of control
potential .at pin 16 from 2 to 4V gives -17 to +3dB
gain variation of the luminance channel. A similar
variation in the chrominance channel occurs in order to
provide correct tracking between the two signals.
LUMINA.NCE
INPUT
SIGNAL
lUMINAN([
OUTPUT
Me
.-.D.
BLACK LEV[l
J"""l.. (lAMP PULSE
'"
GATING PULSE
J\..
1l
BLANKING
PULSE
(HROMtNAN(£
AND BURST
SIGNAL
CONTRAST
SATURATION
BRIGHTNESS
Fig. 5 Application and test circuit
ABSOLUTE MAXIMUM RATINGS
Supply voltage
Total power dissipation
Storage temperature
Operating ambient temperature
256
14V
930mW
-55°C to +125°C
-10°C to +65°C
OPERATING NOTES
1. The gain of the luminance amplifier can be adjusted.
by setting the gain of the contrast control circuit with
selection of the discrete resistor RG (see Fig. 5). This
circuit configuration has been chosen to reduce the
spread of the gain to a minimum (main cause of spread
is the spread of the ratio of the delay line matching
resistors and the resistor RG). At RG ~ 2.7k 0 the
output voltage at,nominal contrast (maximum -3dB)
is 3V black-to-white for an input current 0.2mA blackto-white.
2. The pulse applied to pin 7 is used for gating of the
chrominance amplifier and black level clamping. The
latter function is actuated at a + 7V level. The input
pulse must have such an amplitude that the clamping
circuit is· active only during the back porch of the
blanking interval. The gating pulse switches the gain of
the chroma amplifier to maximum during the flyback
time, when the pulse rises above 2.3V and switches it
back to normal setting when the pulse falls below 1 V.
3. The blanking pulse (pin 9) is used for blanking the
luminance amplifier. When the pulse exceeds the 2.5V
level the output signal is blanked to a level of about·
OV. When the input exceeds a +6V level a fixed level
of typo + 1 .5V is inserted in the output signal. This
level can be used for clamping purposes.
4. The chrominance and burst signal are both available
on pin 6. The burst signal is not affected by the contrast
and saturation control and is kept constant by the ACC
circuit of the TDA2522. The output of the delay line
matrix circuit. which is the ,input of the TDA2522, is
thus automatically compensated for the insertion
losses. This means that the output signal of the TDA
2560 is determined by the insertion losses of the delay
line. At nominal contrast and saturation setting the
ratio of burst to chrominance signal at the output is
typically indentical to that at the input.
5. Nominal contrast is specified as maximum contrast
-3dB. Nominal saturation is specified as maximum
saturation -6dB.
6. A negative-going control voltage gives a decrease in
gain.
CONSUMER
TV CIRCUITS
TDA2590
LINE OSCILLATOR COMBINATION
The TDA2590 is an integrated line oscillator circuit
for colour television receivers using thyristor or transistor line deflection output stages.
The circuit incorporates a line oscillator which is
based on the threshold switching principle, a line deflection output stage capable of direct drive of thyristor
deflection circuits, phase comparison between the
oscillator voltage and both the sync pulse and line
flyback pulse. Also included on the chip is a switch for
changing the filter characteristic and the gate circuit
when used for VCR.
tVESUPI'lY( I
UNEOiP tVESUPPlY[ ,
LINE DRIVE PULSE [
I
PULSE ~ATION SWITCH [
.j
DECOUPIING
UNE FLYBACK PULSE
aURST GATING AND BLANKING f'tllSE
VERTICAL SYNC PULSE
\
,
8
'"
GROUND
'I
CSC.FREa CONTROL
"n
DECOUPl.ING
"
TIME CONSTANT SWITCH
"
"
9
PHASE COMPARISON
VCR SWITCH
NOISE SEPAJIATOR VP
SYNC. SEPARATOR 1/1'
DP16
Fig. 1 Pin connections (top view)
FEATURES
QUICK REFERENCE DATA
II
II
•
II
Coincidence Detector
II Sync Separator
II
II
II
II
II
II
II
III
Noise Separator
Vertical Sync Separator
Colour Burst Keying
Line Flyback
Pulse Generator
Output Pulse Phase Shifter
Output Pulse Duration Switching
Sync Gating Pulse Generator
Low Supply Voltage Protection
Supply Voltage (pin 1)
12V typo
Supply Current
30mA typo
Sync Separator Input (pin 9) 3V p-p typo
II Pulse Duration Switch Input (pin 4)
at t = 6f1s
9.4V to Vl
at t = 14f1s + td
OV to 4V
.. VCR Switch ON (pin 11) OV to 1.5V and
9V to Vl
Output signal
•
Vertical Sync Pulse (pin 8)
II
II
11 V p-p (typ.)
Burst Gating Pulse (pin 7) 11 V p-p (typ.)
Line Drive Pulse (pin 3) 1O.5V p-p (typ.)
ABSOLUTE MAXIMUM RATINGS
Voltages
Supply pin 1 (when supplied by the IC)
13.2V
Supply pin 2
laV
Pin 4
OV to 13.2V
Pin 9
-6V to +6V
Pin 10
-6V to +6V
Pin 11
OV to 13.2V
Currents
Pin 2
400mA peak
Pin 3
400mA peak
Pin 4
lmA peak
Pin 6
10m,A peak
Pin 7
10mA peak
Pin 11
2mA peak
Power dissipation
Total power dissipation
aOOmW
Temperature
Storage temperature
-55°C to +125°C
_10°C to +60°C
Operating ambient temperature
257
TDA2590
tlPIN 1; POINT AI
.r:-L
n.
VERTICAL
SYNC PULSE
BURST GATING
ANO
BLANKING
I""'t PULS £
J\
TO lINf
lINE flYSA(k
PULSE
OHU(TION
n
r----¢~---------Q~----------Q~---------¢,~---------¢'
n____
VIC£O INPUT'-t--i_____
• SHORT-(III(Un
j,FOR
'0.
"
~
+ IPIN I,POINT Al
,----
"
I
1
+IP1H I,PCHH Al
ADJUST
Fig. 2 TDA2590 block diagram
LINE DRIVE PULS:...J
TYP ~p+14J.1s
L
VH6<4V
I'
LINE DRIVE PULS~
6ys
V4-\6>94V
L-
ld 0 -l~
JJ~
I'
--IL---- .
FLYBACK PULSE ___________________________
'I'
'I
=-:J
TYPIC,I,tr I: 12'OJls
L
~i
SYNC PULSE
I
6
BURST I BLANKING
PULSE
ISANOCASTlEI
_____________________________.J
_______
1
"""-----j
~~lIV
f
Fig. 3 TDA2590 timing relationships
258
TDA2590
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Supply voltage, V1 = 12V
Tamb = +25°C
Refer to timing diagram, Fig. 3 and Application circuit. Fig. 4
Voltages are referred to pin 6
Value
Characteristic
Sync separator
Input switching voltage
I nput keying current
Input blocking current
Input switching current
Noise separator
Input switching voltage
Input keying current
Input switching current
Input blocking current
Line flyback pulse
Input current
Input switching voltage
Input limiting voltage
Input resistance
Pulse duration switch
Input voltage
Input current
Input voltage
Input current
Input voltage
Input current (input open)
VCR switch
Input voltage (typical range)
Input current
Output current
Vertical sync pulse (positive going)
Output voltage
Output resistance
Burst gating pulse (positive-going)
Output voltage
Output resistance
Blanking pulse
Output voltage (typical range)
Output resistance
Line drive pulse (positive going)
Output voltage
Output current (average value)
Output resistance for leading edge
of line pulse
Output resistance for trailing edge
of line pulse
Oscillator
Threshold voltage low level
Threshold voltage high level
Discharge current
Phase comparison (Illl: sync
pulse/oscillator)
Control voltage range (typ)
Control current
Output blocking current
Output resistance
Time constant switch
Output voltage
Output current
Output resistance
Pin
Min.
Typ.
Max.
Units
Conditions
9
V
0.8
100
1
5
5
~A
~A
~A
Vs= -5V
10
V
1.4
100
5
150
~A
I'A
1
~A
V10= -5V
6
~A
10
1.4
-0.7
+1.4
V
V
0
V1
V
400
4
9.4
200
0
200
5.4
t=
6~s
~A
4.0 V
t= 14~s +td
~A
6.5 V
~A
0
t= O,V3= 0
See note 1
11
0
9
200
1
V1
1.5 V
V
~A
2
mA
See note 2
V11 = OVto 1.5V
V11 = 9Vto VI
8
10
11
2
Vp-p
kO
10
11
400
Vp-p
0
400
3.5 Vp-p
0
7
7
2.5
3
Vp-p
mA
10.5
100
2.5
0
20
0
14
4.4
7.6
0.47
V
V
mA
13
8.2 V
2.3 mAp-p
V13=4Vt08V
1
I'A
High (see note 3)
V13=4Vt08V
Low (see note 4)
V13 <3.8Vor >8.2V
3.8
1.9
2.1
12
6
1
100
60
V
mA
0
kO
VII = 2.5V to 7V
V11 < 1.5Vor >9V
259
TDA2590
ELECTRICAL CHARACTERISTICS (Contd.)
Characteristic
Pin
Coincidence detector (03)
Output voltage typical range
Output current:
without coincidence
with coi ncidence
Phase comparison (02: oscillator/
line flyback pulse)
Control voltage range (typ)
Control current
Output resistance
11
Value
Min.
Typ.
Max.
0.5
6
V
5
7.6 V
mAp-p
1
V5 = 5.4Vto 7.6V
High (see note 3)
kO
8
Vs < 5.4Vor > 7.6V
5.4
5
~A
1
5
3
7
100
Vp-p
1
5
3
7
100
7
Vp-p
~A
10
12
~s
ton
8
8
~A
Vp-p
11
2
~s
Vp-p
kO
15.625
kHz
±5
%
C14= 4.7nF, R,S = 10kO
See note 5
Hz/~A
31
%
±10
±0.05
260
Vs= 5.4Vt07.6V
9
I'1V/Vnom
Change of frequency when
V, drops to 5V
Temperature coefficient of
oscillator frequency per DC
Phase comparison (01: sync
purse/oscillator)
Control sensitivity
Catching and holding range
(82kO between pins 13 and 15)
Spread of catching and holding range
Phase comparison (02: oscillator/
line flyback pulse)
Permissible delay between leading
edge of output pulse and leading
edge of flyback pulse. I'1td
Static control error. td/td
Overall phase relation See Note 6
Phase relation between middle of
sync pulse and the middle of the
flyback pulse, t
Tolerance of phase relation I'1t
Adjustment sensitivity of
overall phase relation
caused by: adjustment voltage
I'1V5/l'1t
adjustment current,
1'115/l'1t
Conditions
mAp-p
mAp-p
0.1
0.5
Input current at blocked phase
detector
Applications (see Fig. 4)
Sync separator
Input voltage (negative video signal)
Input keying current range
Noise gating
Input voltage
Input keying current range
Superimposed noise voltage
Vertical sync pulse separator
Delay between leading edge of input
and output signal. ton
Delay between trailing edge of input
and output signal, toff
Output voltage
Output resistance
Oscillator
Frequency: free running
Spread of frequency. I'1fo/fo
Frequency control
sensitivity, I'1fo/l'1hs
Adjustment range of
network in Fig. 2
Influence of supply voltage
on frequency Mo/fo
Units
±10
See note 5,V1 = 12V
%
See note 5
±1Q-4
kHz/~s
2
±780
±10
0
Hz
%
15
~s
0.2 %
2.6
~s
0.7
~s
5
0.1
30
V/~s
~A/~s
R'3-1S=82kO
See note 5
TDA2590
ELECTRICAL CHARACTERISTICS (Contd.)
/
Characteristic
Pin
Burst gating pulse
Phase relation between middle of
sync pulse at the input and the
trailing edge of the burst gating
pulse
Phase relation between middle of
sync pulse at the input and the
leading edge of the burst gating
pulse
Line drive pulse
Output pulse duration, tp for thyristor OIP
Output pulse duration, tplfor transistor OIP
Supply voltage for switching
off the output pu Ise
Internal gating pulse
Pulse duration
Value
Units
Conditions
Min.
Typ.
Max.
7
5.8
6.6
7.4
ps
At 7V level
7
1.0
1.9
2.8
ps
At 7V level
3
3
4,5
6.0
14+td
7.5
ps
ps
V4 >9.4V
V4 <4V, see note 7
V7=7V
1
4
V
7.5
ps
NOTES
1.
2.
3.
4.
5.
6.
May also be left unconnected
VCR 'on' is normally achieved by connecting pins 11. via the VCR switch. to either ground or Vl
Current source
Emittp.r follower
Excluding external component tolerances
The adjustment of the overall phase relation and consequently the leading edge of the output pulse occurs automatically by phase
detector 2 (see Fig. 2)
7. td = switch-off delay of line output stage.
-tIPI'" 11
LINE FLY8ACl(
BURST (jATIN(j
PUlJ\."
-.'""
A~T) BlANI(:NG
PULSE
VERTICAL
SYNC PULSE
116:rt.
VIDEO INPUT
~i'"
lSk
Hk
041)1
;;J;100 P
Fig. 4 Application and test circuit
261
262
CONSUMER
lVCIRcurrs
TDA2591/3
LINE OSCILLATOR COMBINATION
The TDA2591 and TDA2593 are integrated line
oscillator circuits for colour television receivers using
thyristor or transistor line deflection output stages.
The circuits incorporate a line oscillator which is
based on the threshold switching principle. a line deflection output stage capable of direct drive of thyristor
deflection circuits. phase comparison between the
oscillator voltage and both the sync pulse and line
flyback pulse. Also included on the chip is a switch for
changing the filter characteristic and the gate circuit
when used for VCR.
The TDA2593 generates a sandcastle pulse (at pin
7) suitable for use with the TDA2532.
tVESUPPl.Y
-;--'- -r-:: p
GROUND
I"P OSCFREDCONTRDL
LINE DIP +VE SUPPlY
PUtS, MATION SWlTCH
,
OECOUPL\NG
"
POECOUPl.ING
' PPHASE COMPARISON
PTIME CONSTANT SWITCH
,
III
LINE ORIVE PULSE
11
LINE FlYBACKPUlSE
BURST GATING AND BLANKING PULSE
VERTICAL SYNC_PULSE
I.'
IPVCASWITCH
"
I
PNO~E
P SEPARATOR tiP
SEPARATOR VP
SYNC.
Fig. 1 Pin connections (top view)
FEATURES
QUICK REFERENCE DATA
•
•
•
•
•
•
•
Ii
•
•
•
•
•
•
Coincidence Detector
Sync Separator
Noise Separator
Vertical Sync Separator
Colour Burst Keying
Line Flyback
Pulse Generator
Output Pulse Phase Shifter
Output Pulse Duration Switching
Sync Gating Pulse Generator
Low Supply Voltage Protection
DPt6
•
Supply Voltage (pin 1)
12V typo
Supply Current
30mA typo
Sync Separator Input (pin 9) 3V p-p typo
Pulse Duration Switch Input (pin 4)
at t ~= 7fls
9.4V to Vl
at t = 14 flS T td
OV to 4V
VCR Switch ON (pin 11) OV to 1.5V and
9V to V,
Output signal
•
Vertical Sync Pulse (pin 8)
•
•
11 V p-p (typ)
Burst Gating Pulse (pin 7) 11 V p-p (typ.)
Line Drive Pulse (pin 3) 1O.5V p-p (typ.)
ABSOLUTE MAXIMUM RATINGS
Voltages
Supply pin 1 (when supplied by the IC)
13.2V
Supply pin 2
18V
Pin 4
OV to 13.2V
Pin 9
-6V to +6V
Pin 10
-6V to +6V
Pin 11
OV to 13.2V
Currents
Pin 2
400mA peak }
..
400mA peak 650mA thYristor drive only
Pin 3
Pin 4
1 mA peak
Pin 6
10mA peak
Pin 7
10mA peak
Pin 11
2mA peak
Power dissipation
Total power dissipation
800mW
Temperature
_55°C to + 125°C
Storage temperature
_10'oC to +60°C
Operating ambient temperature
TDA2591/ TDA2593
t1PI"!1; POINT A I
BURST GATING
s-L
YERTICAL
AN'
n BLANKING
~
~YN( PULSE
r'LPtilSE
10 LINE
f\ LINE fLYBAC~
J \..PUlSE
OEftf{TlON
n
11
VIDEO INPUT
Vv
'C,
;;
+ (PIN
1 J .,
+IPIN1;POINT Al
I,POINT Al
;J;
1
I
1
Fig. 2 TDA2591/3 block diagram
LINE D~IVE P'JLSE
TYP tp+1' s
I
-.I
L
'0'4-16<4'0'
lP5'5-~
I
I::.
LINE DRIVE PULSE
6jJs
---I
I.
V~-16>
N
1
L-_ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ __
\
ld lI-1S
fl~
'\'
I.~----:_"':'=T='---
FLYBACK PULSE - - - - - - - - - - - - - -...
SYNC PULSE
BURST I BLANKING
ISA~~mTLEI _ _ _ _ _ _ _ _ _ _ _ _ _ _--l
Fig. 3 TDA2591/3 timing relations
264
,I
TDA2591/TDA2593
ELECTRICAL CHARACTERISTICS
Test conditions (unless otherwise stated):
Supply voltage, VI = 12V
Tamb = +25°C
Refer to timing diagram, Fig. 3 and Application circuit, Fig. 4
Voltages are referred to pin 6
Characteristic
Sync separator
Input switching voltage
Input keying current
Input blocking current
Input switching current
Noise separator
Input switching voltage
Input keying current
Input switching current
Input blocking current
Line flyback pulse
Input current
Input switching voltage
Input limiting voltage
Input resistance
Pulse duration switch
Input voltage
Input current
Input voltage
Input current
I nput voltage
Input current (input open)
VCR Switching
Input voltage (typical range)
Input current
Output current
Vertical sync pulse (positive going)
Output voltage
Output resistance
Burst ,gating pulse (positive-going)
,Output voltage
Output resistance
Blanking pulse
Output voltage (typical range) 2591
Output voltage (typical range) 2593
Output resistance
Line drive pulse (positive going)
Output voltage
Output current (average value)
Output resistance for leading edge
of line pulse
Output resistance for trailing edge
of line pulse
Oscillator
Threshold voltage low level
Threshold voltage high level
Discharge current
Phase comparison (01: sync
pulse/oscillator)
Control voltage range (typ)
Control current
Output blocking current
Output resistance
Time constant switch
Output voltage
Output current
Output resistance
Pin
Value
Min.
Typ.
Max.
Units
Conditions
9
V
O.S
100
1
5
5
~A
~A
~A
V9= -5V
10
V
1.4
5
100
150
1
~A
~A
~A
Vl0= -5V
6
~A
10
+1.4
V
V
n
VI
V
1.4
-0.7
400
4
9.4
200
0
200
5.4
t= 7flS
~A
4.0 V
t=14~s+ld
~A
6.5 V
~A
0
11
0
9
200
1
VI
1.5 V
V
~A
2
mA
t=O,V3=0
See note 1
See note 2
VII = OVto 1.5V
Vll=9VtOVl
S
10
11
2
Vp-p
kn
10
11
400
Vp-p
n
400
3.5 Vp-p
5.0 Vp-p
n
7
7
2.5
4.0
3
Vp-p
mA
10.5
100
2.5
n
20
n
14
V
V
mA
4.4
7.6
0.47
13
S.2 V
2.3 mAp-p
VI3=4VtoSV
1
~A
V13= 4Vt08V
High (see note 3)
V13 <3,SVor >S.2V
Low (see note 4)
3.S
1.9
2.1
12
6
1
100
60
V
mA
n
kn
Vl1 = 2.5Vto 7V
Vl1 < 1.5Vor >9V
265
TDA2591/ TDA2593
ELECTRICAL CHARACTERISTICS (Contd.)
Characteristic
Pin
Coincidence detector (03)
Output voltage typical range
Output current:
without coincidence
with coincidence
Phase comparison (1ZI2: oscillator/
line flyback pulse)
Control voltage range (typ)
11
Value
Min.
Typ.
Max.
0.5
6
0.1
0.5
V
mAp-p
mAp-p
5.4
7.6 V
_ A .........
1
"I"'p-tJ
V5= 5.4Vt07.6V
High (see note 3)
kO
8
V5 <5.4Vor > 7.6V
Output resistance
Input current at blocked phase
detector
5
~A
1
5
3
7
100
Vp-p
1
5
3
7
100
7
Vp-p
~A
10
12
~s
ton
11
2
8
8
~A
Vp-p
~s
Vp-p
kO
15.625
kHz
",5
%
%
±0.05
±10
See note 5.V,
266
%
=
See note 5
:i:10-4
2
kHz/~s
±780
±10
0
Hz
%
15
~s
0.2 %
2.6
~s
0.7
~s
5
0.1
adjustment current.
~15/ ~t
C14= 4.7nF. R'5 = 10kO
See note 5
Hz/~A
31
:1:10
~V/Vnom
~V5/ ~t
V5 = 5.4Vto 7.6V
9
Change of frequency when
V, drops to 5V
Temperature coefficient of
oscillator frequency per °C
Phase comparison (0, : sync
pulse/oscillator)
Control sensiti'ifity
Catching and holding range
(82kO between pins 13 and 15)
Spread of catching and holding range
Phase comparison (02: oscillator/
line flyback pulse)
Permissible delay between leading
edge of output pulse and leading
edge of flyback pulse. ~td
Static control error. td/td
Overall phase relation See Note 6
Phase relation between middle of
sync pulse and the middle of the
flyback pulse. t
Tolerance of phase relation ~t
Adjustment sensitivity of
overall phase relation
caused by: adjustment voltage
Conditions
5
Control current
Applications (see Fig. 4)
Sync separator
Input voltage (negative1video signal)
Input keying current range
Noise gating
Input voltage
Input keying current range
Superimposed noise voltage
Vertical sync pulse separator
Delay between leading edge of input
and output signal. ton
Delay between trailing edge of input
and output signal. toff
Output voltage
Output resistance
Oscillator
Frequency: free running
Spread of frequency. ~fo/fo
Frequency control
sensitivity. ~fo/ Uh5
Adjustment range of
network in Fig. 2
Influence of supply voltage
on frequency Mo/fo
Units
30
V/~s
~A/~s
R'3-'5 = 82kO
See note 5
12V
TDA2591/TDA2593
ELECTRICAL CHARACTERISTICS (Contd.)
Pin
Characteristic
Burst gating pulse
Pulse width
Phase relation between middle of
sync pulse at the input and the
leading edge of the burst gating
pulse
line drive pulse
Output pulse duration, tp
7
Value
Min.
Typ.
Max.
3.7
4.0
4.3
Units
~s
Conditions
At 7V level
V7=7V
Supply voltage for switching
off the output pulse
Internal gating pulse
Pulse duration
7
2.15
2.65
3.15
3
3
5.5
7.0
14+td
8.5
1
~s
~s
~s
4
V
7.5
~s
At 7V level
V. >9.4V
V. <4V, see note 7
NOTES
1. May also be left unconnected
2. VCR 'on' is normally achieved by connecting pins 11. via the VCA switch. to either ground or V1
3. Current source
4. Emitter follower
5. Excluding external component tolerances
6. The adjustment of the overall phase relation and consequently the leading edge of the output pulse occurs automatically by phase
detector 2 (See Fig. 2)
7. td = switch-off delay of line output stage.
LIN!
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267
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COMMON 3
NOTE - CASE IS THIRD ELECTRICAL CONNECTION
TO-3
KM 3
.245" / .260" SQUARE
.043" / 0.57"
1.09mm / 1.45mm
6.22mm /6.60mm
.225" / .235" SQUARE
.010" / .020"
5.72mm /5.97mm
0.25mm /0.51mm
-
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PIN No.1
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TAG IDENTIFIE S
PIN No.1
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(EF.
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0.25mm / 0.51mm
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b=
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.229mm / .279mm
2_92mm /3.18mm
.155" / .165"
SQUARE
GOLD
METALLISATION
3.94mm 14.19mm
18 LEAD LEAD LESS CARRIER
GC 18
278
9. Plessey Semiconductors
World Wide
279
280
PLESSEY SALES REPRESENTATIVES:
ALABAMA:
Huntsville
(205) 883-9260
Remco
ARIZONA:
Scottsdale
(602) 948-4404
Faser Technical Sales
CANADA:
Bolton
(416) 857-4302
MacKay Associates
CALIFORNIA:
Goleta
Alhambra
Irvine
Los Angeles
San Diego
(805) 964-8751
(213) 281-2280
(714) 557-4460
(213) 487-1241
(714) 292-8525
The Thorson
The Thorson
The Thorson
The Thorson
The Thorson
Company of
Company of
Company of
Company of
Company of
So_ California
So_ California
So. California
So. California
San Diego
FLORIDA:
Plantation
(305) 473-2101
Gallagher Associates
GEORGIA:
Duluth
(404) 476-1730
Remco
ILLINOIS:
Arlington Heights
(312) 956-1000
Micro Sales Inc.
MARYLAND:
Beltsville
(301) 937-5902
Applied Engineering Consultants
MASSACHUSETTS:
Natick
(617) 655-6080
Wayland Engineering Sales
MICHIGAN:
Brighton
(313) 227-1786
S.A.1. Marketing Corp.
MINNESOTA:
Bloomington
(612) 884-8291
Electronics Sales Agency Inc.
MISSOURI:
Independence
St Louis
(816) 254-3600
(314) 997-1515
Engineering Services Company
Engineering Services Company
NEW MEXICO:
Phoenix
(602) 266-2164
Eltron
NEW YORK:
Plainview
Spring Valley
Skaneateles
(516) 681-3155
(914) 354-6067
(315) 685-5731
Robert Smith Assocs.
Robert Smith Assocs.
Robtron Inc.
NORTH CAROLINA:
Raleigh
(919) 847-5079
Remco
OHIO:
Shaker Heights
Centerville
Zanesville
(216) 751-3633
(513) 435-3181
(614) 454-8942
S.A.1. Marketing Corp.
S.A.1. Marketing Corp.
S.A.1. Marketing Corp.
PENNSYLVANIA
Pittsburgh
Huntingdon Valley
(412) 261-0482
(215) 947-5641
S.A.1. Marketing Corp.
Dick Knowels Associates
TEXAS:
Arlington
Houston
Austin
(817) 640-9101
(703) 772-1572
(512) 451-3325
W. Pat Fralia Company Inc.
W. Pat Fralia Company Inc.
W. Pat Fralia Company Inc.
VIRGINIA:
McLean
(703) 356-6309
Applied Engineering Consultants
PLESSEY DISTRIBUTORS
(Dial direct for orders under 100 pieces and faster delivery)
CALIFORNIA:
Palo Alto
Irvine
(415) 856-9332
(714) 540-9979
Nepenthe
Plessey Semiconductors
CANADA:
Toronto
(416) 364-9281
G.E.C. Canada Ltd.
MARYLAND:
Beltsville
(301) 937-8321
Applied Engineering Consultants
NEW YORK:
Plainview
(516) 249-6677
Plainview Electronic Supply Corp.
TEXAS:
Ft. Worth
(817) 429-8596
Pat co Supply
PLESSEY REGIONAL OFFICES
BRYAN PROCTER
Western Sales Manager
710 Lakeway
Suite 265
Sunnyvale, CA 94086
(408)730-1111
JONATHAN HILL
Midwest Sales Manager
4849 N. Scott
Suite 121
Schiller Park,lL 60176
(312) 6763260/3281
TWX 91()'227-0053
PATREDKO
Eastern Sales Manager
89 Marcus Blvd.
Hauppauge, NY 11787
(516) 273-3060
TLX 961419 TELL USA HAUP
A.J. WILLIS
S.E. Sales/Applications
7094 Peachtree Ind. Blvd.
Suite 295
Norcross, GA 30071
(404) 447-6910
TLX7()'7309
Service NSCs
VERN REEB
Central Sales/Applications
112 East High Street
Hicksville, OH 43526
(419)542-7544
281
282
EUROPE
sales offices
BENELUX Plessey S.A., Chausee de St. Job 638, Brussels 1180, Belgium. Tel: 023745973. Tx: 22100
FRANCE Plessey France S.A., 16)0 Rue Petrar4ue, 75016 Paris. Tel: 7274349 Tx: 62789
ITALY Plessey S.p.A., Corso Sempione 73, 20149 Milan. Tel: 349 1741 Tx: 37347
SCAN 01 NAVIA Svenska Plessey A.B .. Aistrornergatan 39, 4tr, S-112 47 Stockholm 49, (P.O. Box 49023 S-10o 28
Stockholm 49) Sweden. Tel: 08 23 55 40 Tx: 10558
SWITZERLAND Plessey Verkaufs A.G., Glattalstrasse 18, CH-8052 Zurich. Tel: 50 36 55,503682 Tx: 54824
UNITED KIN GOO M Plessey Semiconductors, Cheney Milnor, SWlndon, Wilts. SN2 ZQW Tel: 0793 36251
WEST GERMANY Plessey GmbH., 8 Munchen 40, Motorstrasse 56, Tel: (89) 351 6021/6024 Tx: 5215322
Plessey GmbH, Moselstrasse 18, Postfach 522. 4040 Neuss. Tel: (02101) 44091 Tx: 517844
283
agents
AUSTRALIA Plessey Australia Pty. Ltd .• Components Div .• P.O. Box 2. Christina Road. Villawood. N.S.W. 2163.
Tel: 72 0133 Tx: 20384
AUSTRIA Plessey GesmbH .• Postfach 967. A-l011 Vienna. Tel: 63 45 75 Tx: 75 963
BRAZIL Plessey Brazil. Caixa Postal 7821. Sao Paulo. Tel: (011) 269 0211. Tx: 112338
CANADA Plessey Canada Ltd .• 300 Supertest Road. Downsview. Toronto. Ontario. Tel: 661 3711. Tx: 065-24488
EASTERN EU ROPE Plessey Co. Ltd .• 29 Marylebone Rd .• London NWl 5JU. England. Tel: 01 486 4091.
Tx: 27331
EIRE Plessey Ireland Ltd., Mount Brown, Old Kilmainham. Dublin 8. Tel: 75 8451/2. Tx: 4831
GREECE Plessey Co. Ltd., Hadjigianni Mexi 2. Athens. Tel: (21) 724 3000. Tx. 219251
HONG KONG Plessey Company Ltd., Tugu Insurance Building. 12th floor. 1 Lockhart Road. GPO Box 617
Tel: 5-275555 Tx: 74754
JAPAN Cornes & Co Ltd .• Maruzen Building, 2 Chome Nihonbashi-Dori. C.P.O. Box 158, Chuo-ku. Tokyo 103.
Tel: 272-5771. Tx: 24874
Cornes & Co Ltd., Marden House, C.P.O. Box 329, Osaka. Tel: 532-1 012j1 019. Tx: 525-4496
NETHERLAN DS Plessey Fabrieken N.V., Van de Mortelstraat 6. P.O. Box 46, Noordwijk. Tel: 01719 19207.
Tx: 32008
NEW ZEALAN D Plessey (N.Z.) Ltd., Ratanui Street, Private Bag. Henderson, Auckland 8. Tel: Henderson 64 189.
Tx: 2851
PORTU GAL Plessey Autohlatica Electrica, Portugesa S.A.R.L.. Av. Infant D. Henrique 333. Apartado 1060. Lisbon 6.
Tel: 313171/9 Tx: 12190
SOUTH AFRICA Plessey South Africa Ltd., Forum Building, Struben Street. (P.O. Box 2416) Pretoria 0001
Transvaal. Tel: 34511 Tx: 53-0277
SPAIN The Plessey Company Ltd., Calle Martires de Alcala, 4-3 Dcha., Madrid 8. Tel: 248 12 18 and
248 38 82 Tx: 42701
0
284
distributors
FRANCE Scientech, 11 Avenue Ferdi:li nd Buisson, 75016 Paris. Tel: 609 91 36 Tx: 26042
ITALY Melchioni, Via P. Colletta 39, 20135 Milan. Tel: 5794
SCAN DlIIIAVIA Scans~pply AI S., Nannasgade 20, Dk-2200 Copenhagen, Denmark. Tel: 1-83 5090 Tx: 19037
Oy Ferrado A.B. Nylandsgatan 2C, 00120 Helsinki 12, Finland. Tel: 65 60 05 Tx: 121394
Skandinavisk Elektronikk AI S., Ostre Aker Vei 99, Veitvedt. Oslo 5, Norway. Tel: (02) 15 00 90
Tx: 11963
UNITED KINGDOM (For all circuits except T.V.)
Farnell Electronic Components Ltd., Canal Road, Leeds LS12 2TU Tel: 0532636311 Tx: 55147
Gothic Electronic Components, Beacon House, 'Hampton Street, Birmingham B19 3LP. Tel: 021 2368541 Tx: 338731
Semiconductor Specialists (UK) Ltd" Premier House, Fairfield Road, Yiewsley, West Drayton, Middlesex.
Tel: 0895446415 Tx: 21958
SDS Components Ltd., The Airport, Eastern Road, Portsmouth, Hampshire P03 5QR. Tel: 0705 65311 Tx: 86114
For T.V. circuits only:Best Electronics (Slough) Ltd., Unit 4, Farnburn Avenue, Slough, Bucks SL1 4XU Tel: (0753) 31700/39322
C_P.C. Ltd .. 194-200 North Road, Preston PRl 1YP. Tel: (0772) 55034 Tx: 677122
WEST GERMANY
PLZl Dr. Guenther Dohrenberg, 1000 Berlin 30, Bayreuther Strasse 3. Tel: (030) 21 38 043-45
PlZ2 Nordelektronik GmbH-KG, 2085 Quickborn, Harksheiderweg 238-240. Tel: (04 106) 4031 Tx: 02 14299
PlZ6 Mansfeld GmbH & Co. KG, 6000 Frankfurt. Zohelstrasse 11. Tel: (0611) 4470 20
PlZ7 Astronic GmbH & Co. KG, 7000 Stuttgart-Vaihingen, Gruendgenstrasse 7. Tel: (0711) 734918
PlZ8 Neumuller & Co. GmbH, 8021 Tauskirchen, Eschenstrasse 2. Tel: 0896118231 Tx: 0522106
285
286
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