1982_Linear_Switchmode_Voltage_Regulator_Handbook 1982 Linear Switchmode Voltage Regulator Handbook
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HB206R1 /D1
LINEARISWITCHMODE
VOLTAGE REGULATOR
HANDBOOK
THEORY AND PRACTICE
®
MOTOROLA
LINEARISWITCHMODE
VOLTAGE REGULATOR
HANDBOOK
Principal Contributors:
Jade Alberkrack
Bob Haver
Roger Janikowski
Cal Lidback
Nick Lycoudes
Henry Wurzburg
Circuit diagrams external to Motorola products are included as a means of illustrating
typical semiconductor applications; consequently, complete information sufficient for
construction purposes is not necessarily given. The information in this book has been
carefully checked and is believed to be entirely reliable. However, no responsibility is
assumed for inaccuracies. Furthermore, such information does not convey to the
purchaser of the semiconductor devices described any license under the patent rights of
Motorola Inc. or others.
Second U.S. Edition
First Printing
©MOTOROLA INC., 1982
"All Rights Reserved"
Printed in U.S.A.
Switchmode or SWITCHMODE is a trademark of Motorola Inc.
ii
PREFACE
In most electronic systems, voltage regulation is required for various
functions. Today's complex electronic systems are requiring greater regulating peiformance, higher efficiency and lower parts count. Present
integrated circuit and power package technology has produced IC voltage
regulators which can ease the task of regulated power supply design,
provide the performance required and remain cost effective. Available
in a growing variety, Motorola offers a wide range of regulator products
from fixed and adjustable voltage types to special junction and switching
regulator control ICs.
This handbook describes Motorola's voltage regulator products and
provides information on applying these products. Basic Linear regulator
theory and switching regulator topologies has been included along with
practical design examples. Other relevant topics include: trade-offs of
Linear versus switching regulators, series pass elements for Linear regulators, switching regulator component design considerations, heats inking, construction and layout, power supply supervisory and protection,
and reliability. A Motorola regulator selector guide along with data
sheets and an industry cross-reference are also contained in this handbook.
A transistor and rectifier selector guide for switching regulators of various
configurations and power levels is provided in Appendix A and B.
iii
TABLE OF CONTENTS
Page
Section 1.
Section 2.
Section 3.
Section 4.
Section 5.
Section 6.
Section 7.
Section 8.
Basic linear Regulator Theory •..•....••..•.••..•.•.•••.•..•...•.
The IC Voltage Regulator .•.....•...•••.••.••.•..•••.•.•.•.•.•...
The Voltage Reference ..••...•.•.••....•.••••••.•••.••..•••....•
The Error Amplifier •...•••.•.•.•.•••...•..•.•.•••••.•....••...••
The "'Regulator within a Regulator"' .••......•.•••..•..•...•.•...•.
Selecting a linear IC Voltage Regulator ••..•••..•.••..•..•.•...•••
Selecting the Type of Regulator .•...•...•...•..••.•..••.••.•.••..•
Positive Regulators .............•...•...••••.••...•••..•••
Negative Regulators ..••...•••••.•..•....•..•.......•.•..••
Fixed Output Regulators •....••.•......•.•.....•.....•••.•.
Adjustable Output Regulators .•...•.••.•....•.•••••...•••..
Tracking Regulators ......•...•.•.•.........• , •...••.••..••
Floating Regulators .•.............•..•••.•..••..•..•......
Selecting an IC Regulator •...... , •....••....•...............••...
linear Regulator Circuit Configuration and
Design Considerations ...••..••..••...•.•............•••.•.••
Positive, Adjustable Regulators •••...••••........•.......•.••••.• ,
Negative, Adjustable Regulators .•.•.••.••...••..•.••..•.••....•..
Positive, Fixed Regulators ..•...••...•..•••.••....••.•..•.•..•.••
Negative, Fixed Regulators ••....•.•..••••••.•....•.......•.......
Tracking Regulators .....•...••....••..•.••...........••.•..•••.
Floating Regulators ••.•••...••••••..••....•...•....•....••••.•.
Extending the Output Voltage Range •.•.•.•••..•...•.•..•••.••..•..
Electronic Shutdown ...•.....•.••...•...••..•.•.•......•••.....
General Design Considerations .•.••..•••••.••..•••.•..••••••.•.••
Series Pass-Element Considerations for Unear Regulators ....••.....
Series Pass Configurations •.•.•..••.....•.••••.•.•.•.•...••.•...
Series Pass Element Specifications ......•.........•...•..•..•.•...
Current Limiting Techniques .•...•....•.•.•.....•....••.........•
Constant Current Limiting ••.•.•...•..•...••....••.••••.••••.•.••
Foldback Current Limiting ....•.•...•.......•.•....•.••.•..•..•..
Paralleled Series Pass Elements ...•...•........•••..••...•..•..••
Pass Transistor Selection Guide ...........•.•.......•........•.•.
linear Regulator Construction and Layout .•....•.....•..•.••....•
General Considerations .......•.•...••.•...........•...•.••..•.•
Ground Loops and Remote Voltage Sensing •.•.•..•••..••.•.•....•••
Semiconductor Mounting Considerations ..........••..........•...•
linear Regulator Design Example .......................•...•.•..
IC Regulator Selection .•..•.•....•........•...•.....•.•.•..•.•••
Component Value Determination •.•..•.•.••.....••••....•.••..•..
Input Voltage Constraints ..•....•........•...••.......•.....•..•.
Regulator Output Current versus Package Considerations •...•••.•.•••
Series Pass Element Selection .......•.•.•••.....•.......•.•..••.
Heatsink Calculation •.•..•......•....•.••.••.•...•.•.••.•......
Clamp Diodes ......•...•...•.•..•....•......•••.•.•.•.•..••..•
linear Regulator Circuit Troubleshooting Check list •..•...•........
Designing the Input Supply .•...•.•..•.•......••...•••..••.•..••
Capacitor Input Filter DeSign ..••...•.•..••.......•.•••..•.••.....
Surge Current Considerations ...........•....•...•.•..........•..
Design Procedure •.....••...•...•..••....••.•..•.•......•......
Filter Capacitor Determinations •...•.•.••.•.•..••..•...•.•..
Rectifier Requirements •......•••..••.•...........•........
Transformer Specifications .•......•........•......••.•.....
Design Example ..........••......•••...•.•....•..••.•..•.••...
iv
1
1
1
5
8
11
11
11
11
11
13
13
13
13
15
15
22
24
27
28
30
32
32
34
37
37
38
39
39
42
45
46
51
51
52
55
57
57
57
57
58
59
59
60
61
63
64
68
68
68
69
69
70
TABLE OF CONTENTS (continued)
Section 9.
Switching Regulators versus Unear Regulators ...................... .
The Market ......................................................... .
Comparison with Linear Regulators .................................. .
Page
73
73
73
Section 10.
Switching Regulator Topologies .................................... .
Buck and Boost ..................................................... .
Flyback and Forward Converters ..................................... .
Push-Pull and Bridge Converters ..................................... .
78
80
84
Section 11.
Switching Regulator Component Design Tips ....................... .
Transformers .... , .. , ............................................... .
Transistors ......................................................... .
Rectifiers .......................................................... .
Capacitors and Filters ............................................... .
Control Circuits ..................................................... .
87
87
90
96
98
99
Section 12.
The Future for Switching Regulators ................................ .
103
Section 13.
Switching Regulator Design Examples .............................. .
A Simplified Power-Supply Design
Using the TL494 Control Circuit .................................... .
Application of the TL494 in a 400 Watt and 1000 Watt
Off-Line Power Supply ............................................ .
60-Watt Flyback Switching Power Supply Design ...................... .
Sandwiching the Windings .......................................... .
Advantages of Flyback .............................................. .
Final Results ....................................................... .
105
Section 14.
Section 15.
Section 16.
Section 17.
Section 18.
Power Supply Supervisory and Protection Considerations ............ .
The Crowbar Technique ............................................. .
SCR Considerations ................................................. .
The Sense and Drive Circuit ......................................... .
The MC3424 ....................................................... .
Heatsinking ........................................................ .
The Thermal Equation ............................................... .
Selecting a Heatsink ................................................ .
Custom Heatsink Design ............................................ .
Heatsink Design Example ............................................ .
Regulator Reliability ............................................... .
Quality Concepts ................................................... .
Reliability Concepts ................................................. .
IC Regulator Selection Guides ...................................... .
Adjustable Output Regulators ........................................ .
Fixed Output Regulators ............................................. ,
Speciality Regulators and Switching Regulator Control Circuits ......... .
Regulator Data Sheets ............................................. .
LM109, 209, 309 Positive 3-Terminal Fixed
Voltage Regulators ... , ............................................ .
LM117, 217, 317 3-Terminal Adjustable Output Positive
Voltage Regulators .... " .......................................... .
LM117L, 217L, 317L Low Current 3- Terminal Adjustable
Output Positive Voltage Regulators ................................. .
LM117M, 217M, 317M Medium-Current 3-Terminal Adjustable
Output Positive Voltage Regulators ........................... , ..... .
LM123,A/LM223,A/LM323,A 3-Ampere, 5 Volt Positive
Voltage Regulators ................................................ .
LM137, 237, 337 3- Terminal Adjustable Output Negative
Voltage Regulators ................................................ .
v
77
105
107
112
112
117
117
121
121
122
124
129
135
135
136
138
142
145
145
147
151
151
154
157
161
162
167
175
183
191
197
TABLE OF CONTENTS (continued)
Page
Section 18.
Section 19.
Section 20.
AppendixA.
Appendix B.
(continued)
LM137M, 237M, 337M Medium-Current 3-Terminal Adjustable
Negative Voltage Regulators .......................................
LM140 Series, LM340 Series 3-Terminal Positive
Voltage Regulators ................................................
LM150, 250, 350 3-Terminal Adjustable Output Positive
Voltage Regulators ................................................
MC1463, 1563 Negative Voltage Reg ulators ...........................
MC1466L, 1566L Voltage and Current Regulators..................... .
MC1468, 1568 Dual ±15 Volt Regulators ..............................
MC1469, 1569 Positive Adjustable Regulators .........................
MC1723, C Positive or Negative Adjustable Regulator. . . . . . . . . . . . . . . . . .
MC3420, 3520 Inverter Control Circuit ................................
MC3423, 3523 Overvoltage "Crowbar" Sensing Circuit .................
MC3424,A/MC3524,A/MC3324,A Power Supply Supervisory
Circuit/Dual Voltage Comparator .. , .. .. ... .. .. .. ... .. ... . .. ... . ... .
MC34060, 35060 Switch mode Pulse Width Modulation
Control Circuits...................................................
MC7800 Series 3-Terminal Positive Voltage Regulators ................
MC78LOOC,AC Series 3-Terminal Positive Voltage Regulators..........
MC78MOOC Series 3-Terminal Positive Voltage Regulators .............
MC78TOO Series 3-Terminal Positive Voltage Regulators...............
MC7900C Series 3-Terminal Negative Voltage Regulators ..............
MC79LOOC,AC Series 3-Terminal Negative Voltage Regulators .........
SG 1525A, 1527 A/SG2525A, 2527 A/SG3525A, 3527 A
Pulsewidth Modulator Control Circuit.. ...... . .... .... .. ... .........
SG1526/2526/3526 Pulse Width Modulation Control Circuits ...........
TL431 Series Programmable Precision References. . . . . . . . . . . . . . . . . . . . .
TL494, 495 Switch mode Pulse Width Modulation
Control Circuits. .... .. ... ....... . .. .. .. ....... .. .. . ........ ... ....
j.l78S40 Universal Switching Regulator Subsystem .....................
Package Outline Dimensions .........................................
204
211
221
229
235
238
243
249
254
267
273
276
288
300
307
315
316
325
331
338
346
354
365
369
Voltage Regulator Cross-Reference Guide ............................
375
Switch mode Power Transistor Application Selector Guide .............
381
Motorola Switch mode Rectifiers for
Switching Power Supplies .........................................
387
vi
SECTION 1
BASIC LINEAR REGULATOR THEORY
A. THE IC VOLTAGE REGULATOR
The basic functional block diagram of an integrated circuit voltage regulator is
shown in Figure 1-1. It consists of a stable reference, whose output voltage is VREF,
and a high gain error amplifier. The output voltage, Va, is equal to, or a multiple of,
V REF. The regulator will tend to keep Vo constant by sensing any changes in Vo and
trying to return it to its original value. Therefore, the ideal voltage regulator could
be considered a voltage source with a constant output voltage. However, in practice
the IC regulator is better represented by the model shown in Figure 1-2.
In this figure, the regulator is modeled as a voltage source with a positive
output impedance, Zoo The value of the voltage source, V, is not constant; instead,
it varies with changes in supply voltage, Vee, and with changes in IC junction
temperature, Tj, induced by changes in ambient temperature and power dissipation.
Also, the regulator output voltage, Yo, is affected by the voltage drop across Zo,
caused by the output current, 10. In the following text, the reference and amplifier
sections will be described, and their contributions to the changes in the output
voltage analyzed.
B. THE VOLTAGE REFERENCE
Naturally, the major requirement for the reference is that it be stable; variations in supply voltage or junction temperature should have little or no effect on the
value of the reference voltage, VREF.
The Zener Diode Reference
The simplest form of a voltage reference is shown in Figure 1-3a. It consists of
a resistor and a zener diode. The zener voltage, Vz, is used as the reference voltage.
In order to determine Vz, consider Figure 1-3b. The zener diode, VR1, of Figure
1-3a has been replaced with its equivalent circuit model and the value of Vz is
therefore given by (at a constant junction temperature):
V Z = V BZ
where
+
IzZz
Vee - VBZ
= VBZ + ( R + Zz ) Zz
(1)
VBZ = zener breakdown voltage
Iz = zener current
Zz = zener impedance at Iz
Note that changes in the supply voltage give rise to changes in the zener current,
thereby changing the value of Vz, the reference voltage.
Vee
",:>--"-...("'l
Reference
Vo
Figure 1-1. Voltage Regulator Functional Block Diagram
Vee
rv------4-------~Vo
V; f(Vee. Til
Figure 1-2. Voltage Regulator Equivalent Circuit Model
Vee
Vee
e-----()VZ
~--------~:1VZ
VBZ
(a)
(b)
Figure 1·3. Zener Diode Reference
2
The Constant Current -
Zener Reference
The effect of zener impedance can be minimized by driving the zener diode
with a constant current as shown in Figure 1-4. The value of the zener current is
largely independent of Vee and is given by:
Iz = VBEQI
Rsc
where
(2)
VBEQI = base-emitter voltage of Ql
This gives a reference voltage of:
VREF = Vz
+
VBEQI = VBZ
+ IzZz +
VBEQI
(3)
where Iz is constant and given by equation 2.
The reference voltage (about 7 V) of this configuration is therefore largely independent of supply voltage variations. This configuration has the addjtional benefit
of better temperature stability than that of a simple resistor-zener reference.
Referring back to Figure 1-3a, it can be seen that the reference voltage
temperature stability is equal to that of the zener diode, VR I. The stability of zener
diodes used in most integrated circuitry is about +2.2 m V;oC or = .04%I°C(for a
6.2 V zener). If the junction temperature varies 100°C, the zener, or reference,
voltage would vary 4%. A variation this large is usually unacceptable.
However, the circuit of Figure 1-4 does not have this drawback. Here the
positive 2.2 m V/oC temperature coefficient (TC) of the zener diode is offset by the
negative 2.2 m V;oC TC of the VBE of Ql. This results in a reference voltage with
very stable temperature characteristics.
Vee
e_---OVREF
VR1
RSC
Figure 1-4. Constant Current - Zener Reference
3
The Bandgap Reference
Although very stable, the circuit of Figure 1-4 does have a disadvantage in that
it requires a supply voltage of 9 volts or more. Another type of stable reference
which requires only a few volts to operate was described by Widlar1 and is shown in
Figure 1-5. In this circuit VREF is given by:
VREF = VBEQ3
(4)
hR2
VBEQI - VBEQ2
.
RI
(neglectmg base currents)
h =
where
+
The change in VREF with junction temperature is given by:
~ VREF
=
~ VBE3 + {~ VBEQI
;1 ~ VBEQ2} R2
(5)
It can be shown that,
and
~ VBEQI = ~Tj
K In II
(6)
~ VBEQ2 = ~Tj
K In h
(7)
where
K = a constant
~ Tj =
and'
change in junction temperature
II > h
Combining (5), (6), and (7)
A
L.l
VREF = ~ VBEQ3
+
R2
II
~TjK (RI) 1nTz
(8)
Vee
,-------....----.------0
y
VSEQ1
Figure 1-5. Bandgap Reference
4
V REF
Since Ll VBEQ3 is negative, and with II > Iz, In 11/12 is positive, the net change in
VREF with temperature variations can be made to equal zero by appropriately
selecting the values of II, RI, and Rz.
c.
THE ERROR AMPLIFIER
Given a stable reference, the error amplifier becomes the determining factor in
integrated circuit voltage regulator performance. Figure 1-6 shows a typical differential error amplifier in a voltage regulator configuration. With a constant supply
voltage, Vee, and junction temperature, the output voltage is given by:
Vo = AVOL Vi - ZOL 10 = AVOL {(VREF± VIO) - Va {3} - ZOL 10
where
(9)
A VOL = amplifier open loop gain
VIa = input offset voltage
ZOL = open loop output impedance
{3 = R RI R = feedback ratio ( {3 is always:;;; 1)
1+
10
z
= output current
Vi = true differential input voltage
Manipulating (9)
(VREF± VIa) -
ZOL
-A
VOL 10
Vo = - - - - - - - - - : ; - - - {3 + 1
AVOL
(10)
Note that if the amplifier open loop gain is infinite, this expression reduces to:
(11)
The output voltage can thus be set any value equal to or greater than (VREF± VIO).
Note also that if A VOL is not infinite, with constant output current (a non-varying
output load), the output voltage can still be "tweaked in" by varying RI and Rz,
even though VA will not exactly equal that given by equation 11.
Assuming a stable reference and a finite value of A VOL, inaccuracy of the
output voltage can be traced to the following amplifier characteristics:
1. Amplifier input offset voltage drift The input transistors of integrated circuit amplifiers are usually not perfectly
matched. As in operational amplifiers, this is expressed in terms of an input offset
voltage, VIa. At a given temperature, this effect can be nulled out of the desired
output voltage by adjusting VREF or 1/ {3. However, VIO drifts with temperature,
typically±5 to 15 J.LV;oC, causing a proportional change in the output voltage.
Closer matching of the internal amplifier input transistors, minimizes this effect, as
does selecting a feedback ratio, {3, to be close to unity.
5
Vee
\r---7--....- - Q Vo
(-)
Figure 1-6. Typical Voltage Regulator Configuration
2. Amplifier power supply sensitivity Changes in regulator output voltage due to power supply voltage variations can be
attributed to two amplifier performance parameters: power supply rejection ratio
(PSRR) and common-mode rejection ratio (CMRR). In modern integrated circuit
regulator amplifiers, the utilization of constant current sources gives such large
values of PSRR that this effect on Vo can usually be neglected. However, supply
voltage changes can affect the output voltage since these changes appear as
common mode voltage changes, and they are best measured by the CMRR.
The definition of common mode voltage, VCM, illustrated by Figure 1-7a, is:
VCM = (VI ~ V2) _ (V+ ; V-)
where
(12)
voltage on amplifier non-inverting input
V 2 = voltage on amplifier inverting input
V + = positive supply voltage
V - = negative supply voltage
In an ideal amplifier, only the differential input voltage (V I - V2) has any effect on
the output voltage; the value of VCM would not effect the output. In fact, VCM does
influence the amplifier output voltage. This effect can be modeled as an additional
voltage offset at the amplifier input equal to VcM/CMRR as shown in Figures 1-7b
andl-8. The latter figure is the same configuration as Figure 1-6, with amplifier
input offset voltage and output impedance deleted for clarity and common-mode
voltage effects added. The output voltage of this configuration is given by:
6
V 1 0----4--=__,
v(a)
V"(b)
Figure 1-7. Definition of Common-mode Voltage Error
Vee
(+)
~------------~----~---<)Vo
(-)
Figure 1-8. Common·mode Regulator Effects
7
Vo
= AVOLVi = AVOL(VREF -
VCM
CMRR -
{3Vo)
(13)
Manipulating,
Vo = (VREF {3
where
and
+
VCM
CK1RR)
(14)
1
A VOL
VCC
VCM = VREF-T
(15)
CMRR = common-mode rejection ratio
It can be seen from equations (14) and (15) that the output can vary when Vcc
varies. This can be reduced by designing the amplifier to have a high A VOL, a high
CMRR, and by choosing the feedback ratio, {3, to be unity.
3. Amplifier Output Impedance Referring back to equation (9), it can be seen that the equivalent regulator output
impedance, Zo, is given by:
Zo = dVo= ZOL
(16)
dlo
{3AVOL
This impedance must be as low as possible, in order to minimize load current
effects on the output voltage. This can be accomplished by lowering ZOL, choosing
an amplifier with high AVOL, and by selecting the feedback ratio, {3, to beunity.
A simple way of lowering the effective value of ZOL is to make an impedance
transformation with an emitter follower, as shown in Figure 1-9. Given a change in
output current, dlo, the amplifier will see a change of only dlo/hFEQI in its output
current, 10'. Therefore ZOL in equation (16) has been effectively reduced to
ZorJhFEQI, reducing the overall regulator output impedance, ZOo
D. THE REGULATOR WITHIN A REGULATOR APPROACH
In the preceding text, we have analyzed the sections of an integrated circuit
voltage regulator and determined how they contribute to its non-ideal performance
characteristics. These are shown in Table 1-1 along with procedures which
minimize their effects.
It can be seen that in all cases regulator performance can be improved by
selecting A VOL as high as possible and {3 = 1. Since a limit is soon approached in
how much A VOL can be practically obtained in an integrated circuit amplifier,
selecting a feedback ratio, {3, equal to unity is the only viable way of improving
total regulator performance, especially in reducing regulator output impedance.
However, this method presents a basic problem to the regulator designer. If the
configuration of Figure 1-6 is used, the output voltage cannot be adjusted to a value
other than VREF. The solution is to utilize a different regulator configuration known
as the "regulator within a regulator approach."2 Its greatest benefit is in reducing
total regulator output impedance.
8
Vee
VREF
10
•
(-)
R2
Figure 1-9. Emitter Follower Output
TABLE 1-1
VoCHANGES
SECTION
EFFECT CAN BE
INDUCED BY
MINIMIZED BY SELECTING
Vee
1. Constant current-zener method
2. Bandgap reference
Tj
1. Bandgap reference
2. TC compensated zener method
Reference
Amplifier
Vee
1. High CMRR amplifier
2. High AvoL amplifier
3. {3 = 1
Tj
1. Low VIO drift amplifier
2. High AvoL amplifier
3. {3 = 1
1.
2.
3.
4.
10
9
Low ZOL amplifier
High AVOL amplifier
Additional emitter fol/ower output
{3 = 1
Vo
As shown in Figure 1-10, amplifier Al sets up a voltage, VI, given by:
R2
VI = VREF (1 + Ri)
(17)
V I now serves as the reference voltage for amplifier A2, whose output voltage, Va,
is given by:
R2
(18)
Vo= VI= VREF (1 + Ri)
Note that the output impedance of A2, and therefore the regulator output impedance, has been minimized by selecting A2's feedback factor to be unity; and that
output voltage can still be set at voltages greater than VREF by adjusting RI and R2.
A2 -
-
J\jV\r--~--'--Q Vo
V1
A1
> - - -.......--1+
Figure 1-10. The "Regulator within a Regulator" Configuration
'Widlar, R. J., "New Developments in Ie Voltage Regulators," IEEE Journal of Solid State Circuits, Feb. 1971,
Vol. SC-6, pgs. 2-7.
2Tom Fredericksen, IEEE Journal of Solid State Circuits, Vol. SC-3, Number 4, Dec. 1968, "A Monolithic High
Power Series Voltage Regulator."
10
SECTION 2
SELECTING A LINEAR IC VOLTAGE REGULATOR
A. SELECTING THE TYPE OF REGULATOR
There are five basic linear regulator types; these are the positive, negative,
fixed output, tracking and floating regulators. Each has its own particular characteristics and best uses, and selection depends on the designer's needs and trade-offs
in performance and cost.
1. Positive Versus Negative Regulators.
In most cases, a positive regulator is used to regulate positive voltages and a
negative regulator negative voltages. However, depending on the system's grounding requirements, each regulator type may be used to regulate the "opposite"
voltage.
Figures 2-1 a and 2-1 b show the regulators used in the conventional and
obvious mode. Note that the ground reference for each (indicated by the heavy line)
is continuous. Several positive regulators could be used with the same input supply
to deliver several voltages with common grounds; negative regulators may be
utilized in a similar manner.
If no other common supplies or system components operate off the input
supply to the regulator, the circuits of Figures 2-1c and 2-1d may be used to regulate
positive voltages with a negative regulator and vice versa. In these configurations,
the input supply is essentially floated, i.e., neither side of the input is tied to the
system ground.
There are methods of utilizing positive regulators to obtain negative output
voltages without sacrificing ground bus continuity; however, these methods are
only possible at the expense of increased circuit complexity and cost. An example
of this technique is shown in Section 3.
2. Three Terminal, Fixed Output Regulators
These regulators offer the designer a simple, inexpensive way to obtain a
source of regulated voltage. They are available in a variety of positive or negative
output voltages and current ranges. The advantages of these regulators are:
a)
b)
c)
d)
Easy to use.
Internal overcurrent and thermal protection.
No circuit adjustments necessary.
Low cost.
Their disadvantages are:
a) Output voltage cannot be precisely adjusted. (Methods for obtaining adjustable outputs are shown in Section 3).
b) Available only in certain output voltages and currents.
c) Obtaining greater current capability is more difficult than with other
regulators. (Methods for obtaining greater output currents are shown in
Section 3.)
11
Positive
Regulator
Input
Supply
) V;N
1
.-
.L
(a)
~O
)
.L
Positive Output Using Positive Regulator
Input
Supply
V~N) ~
I
~)v~o
Negative
Regulator
(b)
Negative Output Using Negative Regulator
Input
Supply
)
+
T
VIN
.
Negative
Regulator
(e)
)
+
Vo
.
.b
-
Positive Output Using Negative Regulator
Input
Supply
)
Positive
Regulator
+
VIN
.
1
(d)
Negative Output Using Positive Regulator
Figure 2·1. Regulator Configurations
12
~)v~
3. Three Terminal, Adjustable Output Regulators
Like the three terminal fixed regulators, the three terminal adjustable regulators are easy and inexpensive to use. These devices provide added flexibility
with output voltage adjustable over a wide range, from 1.2 V to nearly 40 V, by
means of an external, two-resistor voltage divider. A variety of current ranges
from 100 rnA to 3.0 Amperes are available.
4. Tracking Regulators
Often a regulated source of symmetrical positive and negative voltage is
required for supplying op amps, etc. In these cases, a tracking regulator is required.
In addition to supplying regulated positive and negative output voltages, the
tracking regulator assures that these voltages are balanced; in other words, the
midpoint of the positive and negative output voltages is at ground potential.
This function can be implemented using a positive output regulator together
with an op amp or negative output regulator. However, this method results in the
use of two IC packages and a multitude of external components. To minimize
component count, an IC is offered which performs this function in a single package:
the MC1568/MC1468 ± 15V tracking regulator.
5. Floating Regulators
If the desired output voltage is in excess of 40 volts, a floating regulator such
as the MC 1566/MC 1466 should be considered. The output voltage of this regulator
can be any magnitude and is limited only by the capabilities of an external
transistor. However, an additional floating low voltage input supply is required.
B. SELECTING AN Ie REGULATOR
Once the type of regulator is decided upon, the next step is to choose a
specific device. As an aid in choosing an appropriate IC regulator, a Selection
Guide is contained in Section 17.
To provide higher currents than are available from monolithic technologies, an
IC regulator will often be used as a driver to a boost transistor. This complicates the
selection and design task, as there are now several overlapping solutions to many of
the design problems.
Unfortunately, there is no exact step-by-step procedure that can be followed
which will lead to the ideal regulator and circuit configuration for a specific
application. The regulating circuit that is finally accepted will be a compromise
between such factors as performance, cost, size and complexity.
Because of this, the following general design procedure is suggested:
1. Select the regulators which meet or exceed the requirements for line regulation,
load regulation, TC of the output voltage and operating ambient temperature range.
At this point, do not be overly concerned with the regulator capabilities in terms of
output voltage, output current, SOA and special features.
2. Next, select application circuits from Section 3 which meet the requirements
for output current, output voltage, special features, etc. Preliminary designs using
the chosen regulators and circuit configurations are then possible. From these
designs a judgement can be made by the designer as to which regulator - circuit
configuration combination best meets his requirements in terms of cost, size and
complexity.
13
14
SECTION 3
LINEAR REGULATOR CIRCUIT CONFIGURATION
AND DESIGN CONSIDERATIONS
Once the IC regulators, which meet the designer's performance requirements,
have been selected, the next step is to determine suitable circuit configurations.
Initial designs are devised and compared to determine the IC regulator/circuit
configuration that best meets the designer's requirements. In this section, several
circuit configurations and design equations are given for the various regulator
ICs. Additional circuit configurations can be found on the device data sheets (see
Section 18). Organization is first by regulator type and then by variants, such as
current boost. Each circuit diagram has component values for a particular voltage
and current regulator design.
A. Positive, Adjustable
B. Negative, Adjustable
C. Positive, Fixed
D. Negative, Fixed
E. Tracking
F. Floating
G. Special
1. Obtaining Extended Output Voltage Range
2. Electronic Shutdown
H. General Design Considerations
It should be noted that all circuit configurations shown have constant current
limiting; if foldback limiting is desired, see Section 4C for techniques and design
equations.
A. POSITIVE, ADJUSTABLE OUTPUT IC REGULATOR
CONFIGURATIONS
1. Basic Regulator Configurations
Positive Three-Terminal Adjustables
These adjustables, comprised of the LM117L, LM117M, LMI17, and
LM150 series devices range in output currents of 100mA, 500mA, l.5A, and
3 .OA respectively. All of these devices utilize the same basic circuit configuration
as shown in Figure 3-1A.
MCl723(C)
The basic circuit configurations for the MC 1723(C) regulator are shown in
Figures 3-3A and 3-2A. For output voltages from = 7 V to 37 V the configuration
of Figure 3-2A can be used, while Figure 3-3A can be used to obtain output
voltages from 2 V to = 7 V.
MC1569, MC1469
Figure 3-4A shows the basic circuit configuration for the MC1569, MC1469
regulator IC. Depending on YIN, TA, heatsinking and package utilized, output
currents in excess of 500 rnA can be obtained with this configuration.
15
2. Output Current Boosting
If output currents greater than those available from the basic circuit configurations are desired, the current boost circuits shown in this section can be used. The
output currents which can be obtained with these configurations are limited only by
the capabilities of the external pass element(s).
LMl17L
LMl17M
LMl17
LM150
IAdj
+ Vo
Vout
Rl
240
+
Adjust
+ **
Co
1 J.LF
* Cin is required if regulator is located an appreciable distance from power
supply filter.
** Co is not needed for stability, however it does improve transient response.
t CAdj is not required; however, it does improve Ripple Rejection
Vout
=
1.25V (1
+
:~)
+ IAdjR2
Since IAdj is controlled to less than 100 ~A. the error associated with this term
is negligible in most applications.
Figure 3-1A -
Basic Configuration for Positive, Adjustable Ouput
Three-Terminal Regulators
16
Pin Numbers Adjacent to Terminals are for the Metal Package.
Pin Numbers in Parenthesis are for the Dual In-Line Package.
Vin +20V
(12) 8
6 (10)
RSC
(11 )7
10(2)1
220
ISC=30mA
1 (3)
MC1723
(MC1723C)
?>(6) 4
R3 >5.1 k
_ Va +15V
R1
12K
2(4)
!
_;f
(5) 3
0.01 j.lF
100 pF
9 (13)
Cref
10k. R2
(7)51
R
sc
-=-
~ 0.66V; 10kO(6) 4
R1 5.1 k
MC1723
(MC1723C)
ISC=30mA
1 (3)
3.6k
R3
~
inF
I=
-=
R2
220
1
I
sc
10(2)]
9(13)
C r e C : 13K
R
RSC
2 (4)
(5) 3
0.01 j.lF
6 (10)
1--o-....--'\/'I,'V--1~....... Va +5V
+ V in ........--o----i
~ 0.66V . 10kO----<..---1.-2...0"""'.-1/":""2-W
.....MPS 6512
4
or Equlv
+10 V
6
.... +5 V
ISC =.5 A
MC1569
MC1469
3k
Al
9
5
8
7
CN
10.1 p.F
Vo
A2 = 6.8 k; Al = ( - - -1) A2"" (2VO -7) kO
VAEF
06
CN = 0.1 p.F; CC;;' InF; ASC ""IS'C
See Section 3H for General Design Consldera'tlons
Values shown are for a 15V.500mAI regulator using a MCl569A on a 3°C/W heatslnk at TA up to +70o C
Figure 3-4A. MC1S69, MC1469 Basic Circuit Configuration
Pin Numbers Adjacent to Terminals are for the Metal Package.
Pin Numbers In Parenthesis are for the Dual In· Line Package
Ql
ASC
r-----------------~
2N3055
+VIN
(12) 8
Vo
+15V
1.30
1/2 W
or Equiv
.-----------,
ISC=·5A
+20V
10 (2)
(11) 7
1 (3)
MC1723
(MC1723C)
A3
5.1 k
Al
12k
A2
10k
2 (4)
(6) 4
100pF
.......-0--1
9 (13)
ASC"" 0.66V ; 10kO--.
Vln1
R2
2
1
R2=6.8k.; R1=(VVO .1 )xR2=«2VO·7)kU; CN=0.1JJF; C6"lnF , RSC=<01 .6V
REF
SC
R",?~~VA~
Selection of Q1 based on considerations of Section 4
See Section 3H for General Design Considerations
Values shown are for a 15V, 5AJ regulator using an MC1469R on a 26° C/W heatsink and 01 mounted on a
1 ° C/W heatslnk for T AMAX = + 0° C
Figure 3·10A. MC1569, MC1469 High Efficiency Regulator Configuration
21
B. NEGATIVE, ADJUSTABLE OUTPUT IC REGULATOR
CONFIGURATIONS
1. Basic Regulator Configurations
MC1563, MC1463
Figure 3-1B illustrates the basic circuit configuration for the MC1563,
MC1463 negative regulator IC. Output currents in excess of 500 rnA can be
obtained depending on input voltage, heats inking and maximum ambient
temperature.
--
-
GND
1
-
2
±0.1/oLF
Cn
3
Case
6.8 k
AB
3.3k
AA
1
4
7
-
10V
V' n
Cc
InF
9
Co
-
10
/oL F
--r:
MC1563
MC1463
8
-1:-
T
+
5
6
-5.2 V
ISC=1 25mA
Vo
AS -10n
Vo
AB=6.8kn ;AA=ABX(-V -1 )90(2/VO/-7)kn
AEF
1 •4V
CN=0.1/oLF ; CC;;;' InF ; ASC "" 1
SC
See Section 3H for General Design Considerations
Values shown are for a !-5.2V, 125mA! regulator using a MC1463R at T A up to +70 0 C
Figure 3-1B.
MC1563, MC1463 Basic Regulator Configuration
MCI723(C)
Although a positive regulator, the MCl723(C) can be used in a negative
regulator circuit configuration if the superior regulation and performance capabilities of the MC1563 are not needed. This is done by using an external pass
element and a zener level shifter as shown in Figure 3-2B. It should be noted that
for proper operation, the input supply must not vary over a wide range, since the
correct value for Vz depends directly on this voltage. In addition, it should be
noted that this circuit will not operate with a shorted output.
2. Output Current Boosting
Figure 3-3B shows a configuration for obtaining increased output current
capability from the MC1563, MC1463 regulator by the use of an external series
pass element(s).
22
(12) 8
6 (10)
(11) 7
R1
=
12k
2 (4)
MC1723
....(6_)-(4~~ (MC 1723C)
+
10"F
(5) 3
5(7)
Vo = -15V
2N3055
or Equiv
Vin = -20V to -23V
!VO!~10V; 10knE;;R1+R2E;;100kn; R2= V!~~(R1+R2)"l~~!(R1+R2)
VZE;;!VIN!-VSE(01 )-3V; VZ~!VIN!-!VO !-VSE(01 )+6V
Selection of 01 based on considerations of Section 4
See Section 3H for· General Design Considerations
Warning: Do not short circuit output
Values shown are for a 1-15V.750mAI regulator using the MC1723CL. with 01 mounted on a
20o C/W heatslnk at TA up to +70oC. (DO NOT SHORT CIRCUIT OUTPUT)
Figure 3-2B. MC1723(C) Negative Regulator Configuration
GND
1
::::~0.1ltF
2
3
Case
6.8 k
Rs
3.3 k
R
1
1 N4001 or Equiv
7
CR1
Cc
-10 V
4
lnF
MC1563
MC1463
9
+
Co
A -
ItF
,,!::: 100
8
6
5
~2N3771
.56n.1/2W
ISC=2 .SA
Vo
or Equiv
~
RSC
VO=·S.2Vdc
01
Vo
lAV
Rs=6.8kn; RA=RBX~REF-l)"'(2IVol-7)kn;Cc;;'lnF; RSC'" ISC
CRI: add one diode in series with CRI for each additional base emitter junction in composite 01
Selection of 01 based on considerations of Section 4
See Section 3H for General Design Considerations
Values shown are for a I-S.2V. 2.SA I regulator using an MC1463R (unheatsinked) with 01 mounted
on a 1°C/W heatsink for TA up to +70o C
Figure 3-3B. MC1563, MC1463 Current Boost Configuration
23
C. POSITIVE, FIXED OUTPUT IC REGULATOR CONFIGURATIONS
1. Basic Regulator Configurations
The basic current configuration for the positive three terminal regulators is
shown in Figure 3-1C. Depending on which regulator type is used, this configuration can provide output currents in excess of 3A.
2. Output Current Boosting
Figure 3-2C illustrates a method for obtaining greater output currents with the
three terminal positive regulators. Although any of these regulators may be used,
usually it is most economical to use the 1 ampere MC7800C in this configuration.
VIN
,..1
0
CIN
1.
DEVICE
10
MC78lXX
MC78MXX
MC78XX
MC78TXX
O.lA
O.5A
1.0A
3.0A
---
~
O.33jtF
CO:
XX:
~VO
COl
1
CIN:
,..2
-
3
required if regulator is located more than a few ("'2" to 4") inches away from input supply
capacitor; for long input leads to regulator, up to 1jtF may be needed for CIN' CIN should be a
high frequency type capacitor
improves transient response
these two digits of the type number indicate nominal output voltage.
See Section 3H for General Design Considerations
See Section 17 for available device output voltages
See Section 15 for heatsinking
Figure 3·1C. Basic Circuit Configuration for the Positive, Fixed Output Three Terminal Regulators
VIN
Input
0.12n
5W
MJ2955
orEquiv
+10V
!
Q1
ISC(Ql)
2N6049
2
R
I S C T O T _ Vo
50n
Output + 5V
ISC(iC1 )
XX
=2
digits of type number indicating Voltage. See Section 17 for available device output voltages
R: used to divert IC regulator bias current and determines at what output current level Q1 begins
.
conductlng.O
<
~ VSEON(Q1)
R""I
SIAS(IC1)
;
R
_ 0.6V
I
SC - - , - - j' SCTOT
SC(Q1
=
I
I
SC(Q1)+ SC(IC1)
Selection of Q 1 based on considerations of Section 4
See Section 3H for General Design Considerations
Values shown are for a 15V, 5AJ regulator using an MC7805CK on a 2.5 0 C/W heatsink and Q1 on a
1° C/W heatsink for T A up to 70 C.
Figure 3·2C. Current Boost Configuration for Positive Three Terminal Regulators
24
3. Obtaining an Adjustable Output Voltage
With the addition of an op amp, an adjustable output voltage supply can be
obtained with the MC7805C. Regulation characteristics of the three terminal
regulators are retained in this configuration, shown in Figure 3-3C. If lower output
currents are required, an MC78M05C (O.5A) could be used in place of the
MC7805C.
4. Current Regulator
In addition to providing voltage regulation, the three terminal positive regulators can also be used as current regulators to provide a constant current source.
Figure 3-4C shows this configuration. The output current can be adjusted to any
value from = 8 rnA (IQ, the regulator bias current) up to the available output
current of the regulator. Five volt regulators should be used to obtain the greatest
output voltage compliance range for a given input voltage.
Output
2
Vo
Input
7
0.33/tF
2
0.1
6
/t F
3
f-O-_-<10 k
1 k
See Section 3H for General Design Considerations
Figure 3-3C. Adjustable Ouput Voltage Configuration Using a Three Terminal Positive Regulator
VIN
1
Input
0.33/tF
±
-=
MC7805C
MC78M05C
MC78L05A,C
2
1l
~ Vi)~
R
Vo
liB
-10
Constant
Current to
Grounded Load
Va
I.W'
10=R+IIB; Current Reg 1I10='R0+l:dIB
V O+V 0+2 V";;' V I N";;'35V
See Section 3H for General Design Considerations
Figure 3-4C. Current Regulator Configuration
25
5. High Input Voltage
Occasionally, it may be necessary to power a three terminal regulator from a
supply voltage greater than VIN(MAX) (35V or 40V). In these cases a preregulator
circuit, as shown in Figure 3-5C may be used.
6. High Output Voltage
If output voltages above 24 V are desired, the circuit configuration of Figure
3-6C may be used. Zener diode ZI sets the output voltage, while Ql, Z2, & Dl
assure that the MC7824C does not have more than 30 V across it during short
circuit conditions.
IC1
2N6569
2
MC78XXC
Vo
60V
R1
3
XX=2 digits of type number indicating voltage
VIW30
R1=(1.5)XhFEQ1; VCEOQ1;;'VIN
See Section 3H for General Design Considerations
Values shown for VIN=60V; Q1 should be mounted on a 2°C/W heatsink for operation at T A up to
+700 C. IC1 should be appropriately heatsinked for the package type used.
Figure 3-SC. Preregulator for Input Voltages Above VINMAX
IC1
Vo
2
MC7824CT
48V
IN4001
D1
Z1
I"'"
+
3
0.33 J.lF
oov
IN4749
24V.1W
See Section 3H for General Design Considerations
Values shown are for a\48V. 1Alregulator; Q1 mounted on a 10°C/W heatsink and IC1 mounted on a
2° C/W heatsink for T A up to +70° C.
Figure 3-SC. High Output Voltage Configuration for Three Terminal Positive Regulators
26
D. NEGATIVE, FIXED OUTPUT IC REGULATOR CONFIGURATIONS
1. Basic Regulator Configurations
Figure 3-10 gives the basic circuit configuration for the MC79XX and
MC79LXX three terminal negative regulators.
Output Current Boosting
In order to obtain increased output current capability from the negative three
terminal regulators, the current boost configuration of Figure 3-20 may be used.
Currents which can be obtained with this configuration are limited only by the
capabilities of the external pass transistor(s).
,r
l
se Device
3 or Cr1
!..Q.
Input....
MC79XX 1 A
-VIN
MC79LXXO.1A
Cin
1
O.33J.LF '~
CIN:
CO:
XX:
re Output
-Va
required if regulator is located more than a few inches ("'2" to 4") away from input supply
capacitor; for long input leads to regulator, up to 1J.LF may be required. CIN should be a high
frequency type capacitor.
improves stability and transient response
these two digits of the type number indicate nominal output voltage. See Section 17 for
available device output voltages
See Section 3H for General Design Considerations
See Section 15 for heatsinking
Figure 3-10. Basic Circuit Configuration for the Negative Three Terminal Regulators
-10 V
0.56.1W
Input
( 0.56,lW
VIN
RSC
ISC(Ql)
ISCTOT
>c-====----.=.~ Output
Vo
(
IISC(lCl )
or
Equiv
R
5.6
Gnd
e--------*---~---~_.Gnd
XX= 2 digits of type number indicating output voltage. See Section 2 for voltages available
R;
used to divert regulator bias current and determines at what output current level Q1 begins
VBEON(Ql)
conducting. O 0.5 mAdc will result in a
degradation in regulation.
C R6 is recommended when V 0 > 150
Vdc and should be rated such that Peak
Inverse Voltage> Vo.
01 & 02 selected on the basis of considerations given in Saction 3
See Section 3H for General Design Considerations
Values shown are for a 10 to 250V, 100 mAl regulator using an MC14661. with 01 & 02 mounted
on a 1°C/W heatsink for TA",70"C.
,
Figure 3-1F. MC1566, MC1466 Floating Regulator Configuration
31
o
r-
G. SPECIAL REGULATOR CONFIGURATIONS
1. Obtaining Extended Output Voltage Range
.
As mentioned in the previous section, the output voltage capability of an IC
regulator can be increased by using a level shifting technique. In these circuit
configurations, the IC regulator is powered from a low voltage supply and its
output is shifted by a zener diode to control the base of an external pass element
which regulates the high voltage output. A typical configuration is shown in
Figure 3-1G for an MC1569, MC1469. This technique can be used with any
adjustable output regulator so long as the IC pin voltages, currents, and differentials do not exceed device data sheet specifications.
2. Electronic Shutdown
Occasionally, it is desired that the regulator have an electronic shutdown
feature with which the output voltage can be reduced to zero by an external signal.
=
Vin(1)
2N3738
or Equiv
110Vdc
Vo
5.6
=
100 Vdc
RSC
Q1
4.7 k
R3
Vin(2)
=
30 Vdc
1 N4001
or Equiv
3
,",l
2 k R4
R2
~
9
V1
I
4
6
InF
MC1569
MC1469
(
5
8
\
,.J
t l
43 k
RA
V1
-
7
\ '" J
V1
6.8 k
2
10
0.1 ;tF
RB
R1
-
Selection of Q 1 based on considerations of Section 4
See Section 3H for General Design Considerations
Values shown are for a J100V.80mAI regulator using an MC1469G on a 30 0 C/W heatsink
with Q1 mounted on a 1 C/W heatsink for T A <'70° C,
Figure 3-1G. MC1569, MC1469 Output Voltage Boosting Configuration
32
MC1S69 and MC1S63
These regulators have internal electronic shutdown circuitry. To activate the
shutdown feature, a ImA minimum, lOrnA maximum current is applied to pin 2 of
these regulators. This current may be the output of a logic gate or buffer or other
external circuitry. This feature can be used to obtain thermal shutdown when the
regulator's junction temperature limit is exceeded, as shown in Figures 3-2G and
3-3G; to latch the output when a short circuit occurs, as shown in Figure 3-4G;
or to remotely shut down the regulator during standby periods in battery operated
equipment.
(Shutdown circuitry shown only)
+VIN
6
VIW5. 1v
R 1 '"
IfriiA'"
R3
Vpln2=R2+R3X 5.1V
MC1569
MC1469
V pin2"'1.38V-3.4x 1 0-3(T JMAX-25° C)
Where T JMAX=junction temp. at which
shutdown occu rs
R2+R3"'2.5k
Values shown for T JMAX "'140° C
-::::- --==
Figure 3-2G. MC1569 Thermal Shutdown Configuration
(Shutdown circu itry shown only)
!>
R1'"
5
R1
MC1563
MC1463
-5.1V .....- - - .
R2~2k
<-
>
VIN+5.1V
-SmA
R3
V pin2=R2+'R3x (-5.1 V)
V p in2"'-0.83+1.9x1 0-3(T JMAX-25° C)
where T JMAX=junctlon tamp at which
2
shutdown occurs
-0.61V'--_ _ _ _---'
R2+R3"2.5k
Values shown for T JMAX"1400C
R3> 270
~
-:::-
-=Figure 3-3G. MC1563 Thermal Shutdown Configuration
33
RSC
+VO
r--"9-JV'I./'v--.....,..... (+10 V)
3
+Vin (+15V)
11 k
C1·
4
6
9
MC1569
MC1469
5 -0-... +
1--
:L InF
+ ' - - - -.... +
+
10~F
1;
1·
9k
or IO.1~F
Case
-
6.8 k
2N5223
Co
I1.0~F
5.1 k
pusht-;;il
Re-Start
(Normally "ON")
=
-
·C1 is used to allow automatic "START-UP" when Vin is first applied.
Figure 3-4G. MC1569 Automatic Latch Into Shut-Down When Output Is Short Circuited with
Manual Reset
MCl723
Although the MCl723 does not have internal electronic shutdown circuitry,
this feature can be added externally, as shown in Figure 3-5G. This technique
can be used with any externally compensated regulator IC.
H. GENERAL DESIGN CONSIDERATIONS
In addition to the design equations given in the regulator circuit configuration
panels of Sections 3A-G, there are a few general design considerations which
apply to all regulator circuits. These considerations are given below:
1. Regulator voltages.;.... for any circuit configuration, the worse-case voltages
present on each pin of the IC regulator must be within the maximum and/or
minimum limits specified on the device data sheets. These limits are instantaneous
values, not averages. They include:
a. VINMIN
b. VINMAX
c. (VIN - VOUT) MIN
d. VOMIN
e. VOMAX
For example, the voltage between pins 8 and 5 (VIN) of an MCl723CG must
never fall below 9.5V, even instantaneously, or the regulator will not function
properly.
34
2. Regulator Power Dissipation, Junction Temperature and Safe Operating
Area
The junction temperature, power dissipation output current or safe operating
area limits of the IC regulator must never be exceeded.
Pin Numbers Adjacent to Terminals are for the Metal Package
Pin Numbers in Parenthesis are for the Dual In-Line Package
(Shutdown circuitry shown only)
6 (10)
9 (13)
MC1723
MC1723C
10 k
5 (7)
BV CEO (Q1);;'VO
VCESAT(Q1)";1.0V
@
IC=1mA
Figure 3-5G. MC1723 Electronic Shutdown Configuration
3. Operation with a load common to a voltage of opposite polarity":'- In many
cases, a regulator powers a load which is not connected to ground but instead is
connected to a voltage source of opposite polarity (e.g. op amps, level shifting
circuits, etc.). In these cases, a clamp diode should be connected to the regulator
output as shown in Figure 3-IH. This protects the regulator, during startup and
short-circuit operation, from output polarity reversals.
4. Reverse Bias Protection - Occasionally, there exists the possibility that the
input voltage to the regulator can collapse faster than the output voltage. This could
occur, for example, if the input supply is "crowbarred" during an output overvoltage condition. If the output voltage is greater = 7V, the emitter-base junction of the
series pass element (internal or external) could break down and be damaged. To
prevent this, a diode shunt can be employed, as shown in Figure 3-2H.
Figure 3-3H shows a three-terminal positive-adjustable regulator with the
recommended protection diodes for output voltages in excess of 25 volts, or highoutput capacitance values (Co> 25 f.LF, C Adj > 10 f.LF). Diode D\ prevents Co
from discharging through the regulator during an input short-circuit. Diode D2
protects against capacitor C Adj from discharging through the regulator during an
output short circuit. The combination of diodes D\ and D2 prevents C Adj from
discharging through the regulator during an input short circuit.
35
+VO
Positive
Regulator
+VIN
1 N4001
or
Equiv
-:;
I,
/'
- L-
'V IN1
' endin g on app licatio n
ma Y or rna y not eq ual V IN2· d ~p
Figure 4-1A. NPN Type Series Pass Element Configuration
37
Using a PNP Type Transistor
If the IC regulator does not have an external sense lead, as in the case of
the three terminal, fixed output regulators, the configuration of Figure 4-1B can
be used. (Regulators which possess an external sense lead may also be used with
this configuration.) As before, the PNP type pass element can be a single transistor
or multiple transistors.
External Series Pass Element
VCE(02)
v IN1
UEU
"...
,.......---...
IC(02)
"C"
•
,02/
?
R~
"i
"8"
t
IC Regulator (simplified)
10
18(02)
~
\
VIN1
01 ' -
G~181AS
"0
!I
~
- ...
Figure 4-1 B. PNP Type Series Pass Element Configuration
This configuration functions in a similar manner to that of Figure 4-1 A, in that
the regulator supplies base current to pass element. The resistor, R, serves to route
the IC regulator bias current, IBIAS, away from the base of Q2. If not included,
regulation would be lost at low output currents. The value of R is low enough to
prevent Q2 from turning on when IBIAS flows through this resistor, and is given by:
o < R:,;;; VBE ON (Q2)
(4.0)
IslAS
B. SERIES PASS ELEMENT SPECIFICATIONS
Independent of which configuration is utilized, the transistor or transistors that
compose the pass element must have adequate ratings for IcMAX, VCEO, hFE, power
dissipation, and safe-operating-area.
1. ICMAx -
for the pass element of Figure 4-1A, ICMAX is given by:
1cMAX(Q2)
ICMAX(Q2) ~ lOMAX - IBMAX(Q2) = lOMAX hFE(Q2)
(4.1)
lOMAX
(4.2)
~
For the configuration of Figure 4-1B:
ICMAX(Q2) ~ lOMAX
~
+ IBMAX(Q2)
lOMAX
38
(4.3)
(4.4)
2. V CEO start up:
since VCE(Q2) is equal to VINl(MAX) when the output is shorted or during
V CEO(Q2) :?: VINl(MAX)
3. hFE -
(4.5)
the minimum DC current gain for Q2 in Figures 4-1A and 4-lB is
given by:
ICMAX(Q2) @
hFEMIN(Q2):?: I
VCE = (VINl(MIN) - Yo)
BMAX(Q2)
(4.6)
4. Maximum Power Dissipation, PD(MAX) and Safe-Operating Area (SOA) for any transistor there are certain combinations of Ic and V CE at which it may safely
be operated. When plotted on a graph, whose axes are V CE and Ie, a safe-operating
region is formed.
As an example, the safe-operating-area (SOA) curve for the well known
2N3055 NPN silicon power transistor is shown in Figure 4-2. The boundaries of the
SOA curve are formed by the ICMAx, power dissipation, second breakdown and
V CEO ratings of the transistor. Notice, that the power dissipation and second
breakdown ratings are given for a case temperature of + 25°C, and must be derated
at higher case temperatures. (Derating factors may be found in the transistors' data
sheets.) These boundaries must never be exceeded during operation, or destruction
of the transistor or transistors which constitute the pass element may result. (In
addition, the maximum operating junction temperature must not be exceeded. See
Section 15.)
C. CURRENT LIMITING TECHNIQUES
In order to select a transistor or transistors with adequate SOA, the locus of
pass element Ie and VCE operating points must be known. This locus of points is
determined by the input voltage (VINl), output voltage (Vo), output current (10) and
the type of output current limiting technique employed.
In most cases, VINl, Yo, and the required output current are already known.
All that is left to determine is how the chosen current limit scheme affects required
pass element SOA.
NOTE: Since the external pass element is merely an extension of the Ie
regulator, the following discussions apply equally well to Ie regulators not using an external pass element.
1. Constant Current Limiting
This method is the simplest to implement and is extensively used, especially
at the lower output current levels. The basic curcuit configuration is shown in
Figure 4-3A, and operates in the following manner:
As the output current increases, the voltage drop across Rsc increases, proportionately. When the output current has increased to the point that the voltage drop
across Rsc is equal to the base-emitter "on" voltage of Q3 (VBEON(Q3», Q3
conducts. This diverts base current (IDRIVE) away from Ql, the Ie regulator's
internal series pass element. Base drive (IB(Q2» of Q2 is therefore reduced and its
collector-emitter voltage increases, thereby reducing the output voltage below its
regulated value, Your. The resulting output voltage-current characteristic is shown
in Figure 4-3B. The value of Isc is given by:
I
VBEON(Q3)
sc = ---'R"'s-c-'--'-
39
(4.7)
20
JlIC~AX
"
10
•
" ,
,
'~
V
,
7
5
2N3055
Safe-Operatfng-Area
' . ,,
3
I
E
~
POMAX@ TC=25°C
,
"
,
2
\
,;
c
..t::
a....
B
!
o
o
Second Breakdown @ T C=25° C - -
0.7
-...\,
1
,,
0.5
0.3
0.2
VCE1-
--
0.1
3
4
5
7
10
20
40
Collector-to-Emltter Voltage, V CE (Volts)
Figure 4-2. 2N3055 Safe-Operating-Area
40
60
External Pass Element
IC(Q2)
•
--.
10
VCE(Q2)
,;----.....
AAA
vv
\ I
RSC
Q2
\
t
Qll
Ib(Q2)
VSE(Q3)
~
G
DIDRIVE
/
Q3"
I
I
I
IC Regulator
Figure 4-3A. Constant Current Limiting
VOUT+-----------------------~
"
:l'"
(5
>
0
;>
..
Q.
:J
o
Output Current
ISC
10
Figure 4-38. Constant Current Limiting
By using the base of Ql in the IC regulator as a control point, this configuration has the added benefit of limiting the IC regulator output current (IB(Q2) to
Isc/hFE(Q2), as well as limiting the collector current of Q2 to Isc. Of course, access to
this point is necessary. Fortunately, it is usually available in the form of a separate
pin or as the regulator's compensation terminal. *
The required safe-operating-area for Q2 can be obtained by plotting the V CE
and Ie of Q2 given by:
IcrQ2) = 10
(4.8)
(4.9)
Vo
VOUT for 0 :::; 10 :::; Isc
(4.10)
10
Isc for 0 :::; Vo :::; VOUT
(4.11)
VCE(Q2) = VINl - Vo - IoRsc = VINl - Vo
where
and
*The three terminal regulators have internal current limiting and therefore do not provide access to this point. If an
external pass element is used with these regulators, constant current limiting can still be accomplished by diverting
pass element drive. See Section 3 for circuit techniques.
41
The resulting plot is shown in Figure 4-4. The transistor chosen for Q2 must
have an SOA which encloses this plot, as shown in this Figure.
Note that the greatest demand on the transistors SOA capability occurs when
the output of the regulator is short circuited and the pass element must support the
full input voltage and short circuit current simultaneously.
ICMAX~------------------~
"
, ' / Pass Element SOA
,
'\
..
.I:
.. N
\
u_
"a
.. u
0-
"",
~.2
;3
ISC
\;
I
I
I
I
I
.•
Collector·Emitter Voltage
log VCE(Q2)
VIN1 VCEO
Figure 4-4. Constant Current limit SOA ReqUirements
2. Foldback Current Limiting
A disadvantage of the constant current limit technique is that in order to obtain
sufficient SOA the, pass element must have a much greater collector current
capability than is actually needed. If the short circuit current could be reduced,
while still allowing full output current to be obtained during normal regulator
operation, more efficient utilization of the pass elements SOA capability would
result. This can be done by using a "foldback" current limiting technique instead
of constant current limiting.
The basic circuit configuration for this method is shown in Figure 4-5A. The
circuit operates in a manner similar to that of the constant current limiting circuit,
in that output current control is obtained by diverting base drive away from Ql
with Q3.
At low output currents, VA approximately equals Vo and VR2 is less than than
Yo. Q3 is therefore non-conducting and the output voltage remains constant. As the
output current increases, the voltage drop across Rsc increases until VAand VR2 are
great enough to bias Q3 on. The output current at which this occurs is lK, the
"knee" current.
42
'External Pass Element
..
IC(02)
VCE(02)
~
RSC
G~
\
01
I
IDRIVE
IC Regulator
Figure 4-5A. Foldback Current Limiting
VOUTt------------------------,
"
l'l'"
~
0
..::> >
a-::>
o
ISC
Output Cu rrent
10
Figure 4-58. Foldback Current Limiting
The output voltage will now decrease. Less output current is now required to
keep V A and VR2 at a level sufficient to bias Q3 on since the voltage at its emitter has
the tendency to decrease faster than that at its base. The output current will continue
to "foldback" as the output voltage decreases, until an output short circuit current
level, Isc, is reached when the output voltage is zero. The resulting output currentvoltage characteristic is shown in Figure 4-5B. The values for RI, R2, and Rsc
(neglecting base current of Q3) are given by:
43
Rsc
VOUT/ISC
VOUT
=
(1
Rl
and
where
Rl
+
VOUT
R2:::::;;;
+
vBEON(Q3/ -
(4.12)
IK
Isc
V BEON(Q3)
R2
(4.13)
+ R2 = ----.,.I~sc=.:R;:-.:.s..::.c~
VOUT
(4.14)
IORIVE
= normal regulator output voltage
IK = knee current
Isc
IoRIVE
= short circuit current
= base drive to regulator's internal pass element(s)
A plot of Q2 operating points which result when using this technique are
shown in Figure 4-6. Note that the pass element is required to operate wjth a
collector current of only Isc during short circuit conditions, not the full output
current, IK. This resuts in a more efficient utilization of the SOA of Q2 allowing the
use of a smaller transistor than if constant current limiting were used. Although
foldback current limiting allows use of smaller pass element transistors for a given
regulator output current than does constant current limiting, it does have a few
disadvantages .
.IC(MAX) .....- - - - - - - - -......
,,
,
...c:
I!!... -N
" a
0
.. 0
0-
.. CD
!II
0
8-
Current
Limiting
ISC
VIN1
V'CEO
Collector-Emitter Voltage
log VCE(Q2)
Figure 4-6. Foldback Current LImit SOA Requirements
44
Referring to Equation (4.12), as the foldback ratio, IKiIsc, is increased, the
required value of Rsc increases. This results in a greater input voltage at higher
foldback ratios. In addition, it can be seen for Equation (4.12) that there exists
an absolute limit to the foldback ratio equal to:
IK
VOUT
(Is~ MAX = 1 + VBEON(Q3/or Rsc = 00
(4.15)
For these reasons, foldback ratios greater than 2: 1 or 3: 1 are not usually
practical for the lower output voltage regulators.
D. PARALLELING PASS ELEMENT TRANSISTORS
Occasionally, it will not be possible to obtain a transistor with sufficient
safe-operating-area. In these cases it is necessary to parallel two or more transistors. Even if a single transistor with sufficient capability is available, it is possible
that paralleling two smaller transistors is more economical.
In order to insure that the collector currents of the paralleled transistors are
approximately equal, the configuration of Figure 4-7 can be used. Emitter ballasting resistors are used to force collector current sharing between Ql and Q2.
The collector current mismatch can be detennined by considering the following:
From Figure 4-7,
VBEl
+
+
VI = VBE2
V2
(4.16)
(4.17)
= av
where a VBE = VBEl - VBE2
and
a V = V2 - V I
and
aVBE
,------4~----,-------
+,C2
r----~-~-------
- - --- - --,
i
-----,
I
I
1
:
02
'- - -
I
V".
".J
- - - -ION
VBE~
....
I
'~
,,
~;
<>
~
1
~---..---......
-- - - ------ ---
Figure 4-7. Paralleling Pass Element Transistors
45
,1
Assuming lEI
= ICI and IE2 = Ie2, the collector current mismatch is given by,
Ie2 - leI
Ie2
IVI)
RE!\RE
( V2\
= (~~) =
V2 - VI
V2
~V
=
(4.18)
V2
(4.19)
and,
~VBE
.
percent collector current nnsmatch = ---y-;- x 100%
(4.20)
From Equation (4.20), the collector current mismatch is dependent on ~
VBE and V2. Since ~ VBE is usually acceptable, V2 should be 1.0 V to 0.5 V,
respectively. RE is therefore given by:
RE
= 0.5 to 1.0 V = 0.5
Iel
V to 1.0 V
Ie2
= 0.5
V to 1.0 V
Ic/2
(4.21)
E. TRANSISTOR SELECTION GUIDE
As an aid in selecting an appropriate series pass element, the following
selection guide has been included.
DevIce and Polarity
NPN
PNP
tr
VCEO
Volts
Min
hFE
MiniMax
IC
Amps
Vee(sat)
Volts
Max
Ic
Amps
MHz
Min
Po
Watts
Max
Case
250
350
40/160
40/160
0.02
0.02
0.5
0.5
0.05
0.05
15
15
15
15
77
77
250
300
300
350
30/250
30/250
30/240
30/250
0.1
0.1
0.05
0.1
1.0
1.0
0.1
0.1
10
10
1.0
0.1
10
20
20
20
20
77
77
77
77
40
40
1.0
0.5
1.0
0.5
1.0
0.5
1.0
0.1
0.3
0.3
0.1
0.3
0.7
0.6
0.7
0.6
0.7
0.6
0.7
2.5
1.0
1.0
2.5
1.0
1.0
1.0
1.0
1.0
1.0
1.0
1.0
0.25
1.0
1.0
0.25
1.0
3.0
3.0
3.0
3.0
3.0
3.0
3.0
10
10
10
10
10
30
30
30
30
30
30
30
20
40
40
20
40
221A
60
60
80
80
100
225
250
300
300
350
15/75
30/150
15175
30/150
15/75
30/150
15/75
40/200
30/150
30/150
40/200
30/150
175
250
300
300
40/200
8180
8/80
30/150
0.5
1.0
1.0
0.75
5.0
0.75
0.75
1.0
1.0
1.0
1.0
0.75
10
10
10
15
35
35
35
35
80
80
80
80
750
21
2.5
5.0
2.5
7.5
10
01
0.3Amp
MJE3440
MJE3439
0.5 Amp
2N5655
2N5656
MJE340
2N5657
MJE350
1.0 Amp
TIP29
2N4921
TIP29A
2N4922
TIP29B
2N4923
TIP29C
2N3738
TIP47
TIP48
2N3739
TIP49
TIP30
2N4918
TIP30A
2N4919
TIP30B
2N4920
TIP30C
2N6424
2N6425
77
221A
77
221A
77
221A
80
221A
221A
80
221A
2.0 Amp
2N3583
2N3584
2N3585
2N424O
2N6420
2N6421
2N6422
2N8423
2.5 Amps
BU205
46
PREFERRED SILICON POWER TRANSISTORS (continued)
veEO
tr
Volts
Min
hFE
Ie
MiniMax
Amps
V.slsat)
Volts
Max
Amps
MHz
Min
PD
Watts
Max
30
40
40
60
60
80
80
100
251
251
40/200
30/150
251
251
50/250
251
1.0
1.0
1.5
1.5
1.0
1.0
0.1
1.0
1.2
0.75
0.75
1.2
1.2
0.9
1.2
3.0
1.5
1.5
3.0
3.0
1.5
3.0
3.0
60
60
3.0
3.0
50
3.0
25
40
6.0
6.0
40
40
1.5
40
400
30/90
1.0
0.8
1.0
2.8
100
01
2N5193
2N6034
MJE3310
2N6124
2N6049
2N6125
2N6415
2N5194
2N3740
2N6296
2N6035
MJE3311
MJE700
2N6126
MJE3312
2N5195
2N3741
2N6297
2N6036
40
40
40
45
55
60
60
60
60
60
60
60
60
80
80
80
80
80
80
25/100
750/15K
10001
25/100
25/250
25/100
40/250
25/100
30/100
750/18K
750/15K
1000
7501
20/80
10001
20/80
30/100
750/18K
750/15K
1.5
2.0
1.0
1.5
0.5
1.5
0.2
1.5
0.25
2.0
2.0
1.0
1.5
1.5
1.0
1.5
0.25
2.0
2.0
0.6
2.0
1.5
0.6
1.0
0.6
2.5
0.6
0.6
2.0
2.0
1.5
2.5
0.6
1.5
0.6
0.6
2.0
2.0
1.5
2.0
1.5
1.5
0.5
1.5
4.0
1.5
1.0
4.0
2.0
1.5
1.5
1.5
1.5
1.5
1.0
2.0
2.0
2.0
1.0
20
2.5
3.0
2.5
50
2.0
3.0
50
1.0
20
1.0
2.5
20
2.0
3.0
4.0
1.0
40
40
15
40
75
40
15
40
25
80
40
15
40
40
15
40
25
50
40
77
77
77
MJE210
2N6313
MJE 1090
2N6314
40
60
60
80
225
250
250
275
300
300
325
325
350
350
700
45/180
25/100
7501
25/100
25/125
10n5
51
25/125
10n5
51
25/125
2.0
1.5
3.0
1.5
1.0
2.5
5.0
1.0
2.5
5.0
1.0
2.5
5.0
4.5
2.0
1.5
3.0
1.5
1.0
2.5
5.0
1.0
2.5
5.0
1.0
3.0
2.5
5.0
4.5
65
4.0
lOn5
51
2.251
0.75
0.7
2.5
0.7
0.5
1.0
2.0
0.5
1.25
2.0
0.5
2.0
1.5
2.0
5.0
15
75
70
75
50
80
80
50
5.0
80
50
125
80
80
1.25
Device and Polarity
PNP
NPN
Ie
Case
3.0 Amps
MJE520
MJE31
MJE31A
MJE31B
MJE181
MJE31C
MJE32
2N3867
2N3868
MJE32A
MJE32B
MJE171
MJE32C
77
77
31
31
77
77
77
77
3.5 Amp
2N3902
4.0 Amp
2N5190
2N6037
MJE3300
2N6121
2N3054A
2N6122
2N6413
2N5191
2N6294
2N6038
MJE3301
MJE800
2N6123
MJE3302
2N5192
2N6295
2N6039
221A
80
221A
77
77
80
77
77
77
221A
77
77
80
80
77
5.0 Amp
MJE200
2N4232A
MJEllOO
2N4233A
2N6233
2N6497
MJE51T
2N6234
2N6498
MJE52T
2N6235
MJ3030
2N6499
MJE53T
BU208
47
4.0
20
5.0
2.5
20
80
2.5
20
5.0
2.5
4.0
77
80
90
80
80
221A
221A
80
221A
221A
80
01
221A
221A
01
PREFERRED SILICON POWER TRANSISTORS (continued)
Device and Polarity
PNP
NPN
VCEO
Volts
Min
hFE
MinIMax
".
Amps
Ie
Vcalsatl
Volts
Max
Amps
MHz
Min
PD
Watts
Max
ea..
3.0
3.0
3.0
3.0
3.0
3.0
3.0
1.5
1.5
1.5
1.5
1.0
1.0
1.0
6.0
6.0
6.0
6.0
3.0
3.0
3.0
3.0
3.0
3.0
3.0
1.0
1.0
1.0
2.0
2.0
2.0
2.0
150
150
150
221A
221A
221A
221A
11
11
11
4.0
4.0
4.0
3.0
4.0
4.0
4.0
3.0
3.0
3.0
3.0
2.0
2.0
2.0
2.0
2.0
2.0
2.0
2.0
O.S
1.0
1.5
4.0
4.0
4.0
3.0
4.0
4.0
4.0
3.0
3.0
3.0
3.0
4.0
4.0
4.0
75
100
75
90
75
100
75
75
125
125
125
80
11
221A
11
SO
11
221A
221A
01
01
01
5.0
5.0
4.0
4.0
10.0
10.0
10.0
10.0
4.0
1.0
4.0
5.0
1.0
5.0
5.0
5.0
0.5
1.0
2.0
2.0
1.1
1.1
0.5
0.5
0.5
0.5
1.0
0.8
1.0
2.0
O.S
1.0
1.0
1.0
0.8
0.8
5.0
5.0
4.0
4.0
5.0
5.0
5.0
5.0
5.0
5.0
5.0
5.0
5.0
7.5
7.5
7.5
0.5
1.0
20
20.
2.0
2.0
1.0
1.0
1.0
1.0
4.0
4.0
4.0
20
4.0
1.0
1.0
1.0
2.5
2.5
100
100
11
11
90
221A
340
340
340
340
11
11
11
11
11
11
11
11
11
11
4.0
6.0
6.0
6.0
6.0
6.0
6.0
1.5
0.7
0.7
2.0
0.7
2.0
2.0
4.0
6.0
6.0
6.0
6.0
6.0
6.0
1.5
2.0
2.0
4.0
2.0
4.0
4.0
100
100
100
150
100
150
150
Ie
1.0 Amp
TIP41
TIP41A
TIP41B
TIP41C
2N5758
2N5959
2N5760
TIP42
TlP42A
TIP42B
TIP42C
2N6226
2N6227
2N622S
40
60
80
100
100
120
140
15n5
15n5
15n5
15n5
25/100
20/80
15/60
1.0 Amp
2N6300
2N6055
2N6043
MJ1000
2N6301
2N6056
2N6044
2N6045
2N6306
2N6307
2N6308
2N6298
2N6053
2N6040
MJ900
2N6299
2N6054
2N6041
2N6042
60
60
60
60
SO
SO
SO
100
250
300
350
750l1SK
750/1SK
lK!10K
10001
750l1SK
750/18K
lK!10K
lK!10K
15n5
15n5
12/60
4.0
4.0
4.0
4.0
5.0
5.0
5.0
10.0 Amp
2N6383
2N6384
MJE3055
MJE3055T
MJE4340
MJE4341
MJE4342
MJE4343
2N5877
2N3715
2N5878
2N6385
2N3716
2N5632
2N5633
2N5634
MJ413
MJ423
2N6648
2N6649
MJE2955
MJE2955T
MJE4350
MJE4351
MJE4352
MJE4353
2N5875
2N3791
2N5876
2N6650
2N3792
2N6229
2N6230
2N6231
40
60
60
60
100
120
140
160
60
60
SO
lK!20K
lK!20K
201100
80
80
lK!20K
100
120
140
325
325
251100
20/80
15160
20/80
20/100
501
501
501
501
20/100
50/150
20/100
50/150
'~0/90
90
90
125
125
125
125
150
150
150
100
150
150
150
150
125
125
12.0 Amp
2N6569
2N5989
2N5990
2N6057
2N5991
2N6058
2N6059
2N5986
2N5987
2N6050
2N5988
2N6051
2N6052
40
40
60
60
SO
SO
100
15/200
20/120
20/120
750/18K
20/120
750/1SK
750/1SK
48
11
90
90
01
90
01
01
PREFERRED SILICON POWER TRANSISTORS (continued)
tr
Po
Watts
Max
Case
2.5
2.5
2.5
75
75
115
160
120
75
160
120
120
175
175
175
221A
221A
11
11
11
221A
11
11
11
01
01
01
10
10
10
1.0
1.0
1.0
200
200
200
11
11
11
2.0
1.0
2.0
2.0
10
10
10
10
4.0
2.0
4.0
4.0
160
200
160
160
01
11
01
01
10.0
10.0
10.0
10.0
10.0
10.0
1.0
1.0
1.0
1.0
1.0
1.0
15
15
10
10
10
10
4.0
4.0
40
40
40
40
200
200
200
200
200
200
11
11
01
01
01
01
0.75
0.75
0.8
10
10
7.5
2.0
2.0
2.0
200
200
200
11
11
11
1.0
1.0
1.0
1.0
1.0
1.0
25
25
20
20
20
20
2.0
2.0
30
30
30
30
300
300
250
250
250
250
197
197
197
197
197
197
VCEO
Volts
Min
hFE
MiniMax
IC
Amps
Vee(satl
Volts
Max
IC
Amps
MHz
Min
40
60
60
60
60
80
80
90
120
200
275
350
20/150
20/150
20170
20/100
500/5K
20/150
20/100
500/5K
500/5K
10/50
8/50
6/50
5.0
5.0
4.0
6.0
10.0
5.0
6.0
10.0
10.0
10.0
10.0
10.0
1.3
1.3
1.1
1.0
4.0
1.3
1.0
4.0
4.0
1.5
1.5
1.5
5.0
5.0
4.0
7.0
15
5.0
7.0
15
15
10
10
10
5.0
5.0
2.5
4.0
2N6029
2N6030
2N6031
100
120
140
25/100
20/80
15/60
8.0
8.0
8.0
1.0
1.0
1.0
2N6285
2N5745
2N6286
2N6287
60
80
80
100
750/18K
151160
750/18K
750/18K
10.0
10.0
10.0
10.0
2N5883
2N5884
60
80
100
120
140
150
20/100
20/100
30/120
Device and Polarity
NPN
PNP
15.0 Amp
2N6486
2N6487
2N3055
2N5881
2N6576
2N6488
2N5882
2N6577
2N6578
2N6249
2N6250
2N6251
2N6489
2N6490
MJ2955
2N5879
2N6491
2N5880
5.0
4.0
16.0 Amp
2N5629
2N5630
2N5631
20.0 Amp
2N6282
2N5303
2N6283
2N6284
25.0 Amp
2N5885
2N5886
2N6338
2N6339
2N6340
2N6341
30/120
30/120
30/120
30.0 Amp
2N5301
2N5302
MJ802
2N4398
2N4399
MJ4502
40
60
90
25/100
15.0
15.0
7.5
2N5683
2N5684
60
80
100
120
140
150
15/60
15/60
30/120
30/120
30/120
20/120
25.0
25.0
20.0
20.0
20.0
20.0
15/60
15/60
50.0 Amp
2N5685
2N5686
2N6274
2N6275
2N6276
2N6277
SILICON POWER DEVICE PACKAGES
CASE 1-03
(TO-204AA)
(TO-3)
~~~
CASE 3-04
CASE 54-05
CASE 197·01
(TO-204AA)
(TO-3 TYPE)
~
(TO-213AA)
(TO-66)
49
50
SECTION 5
LINEAR REGULATOR CONSTRUCTION
AND LAYOUT
An important, and often neglected, aspect of the total regulator circuit design
is the actual layout and component placement of the circuit. In order to obtain
excellent transient response performance, high frequency transistors are used in
modern integrated circuit voltage regulators. Proper attention to circuit layout is
therefore necessary in order to prevent regulator instability or oscillations, or
degraded performance.
In this section, guidelines will be given on proper regulator layout and
placement of circuit components. In addition, topics such as remote voltage sensing
and semiconductor mounting techniques will also be considered.
1. General Layout and Component Placement Considerations
As mentioned previously, modern integrated circuit regulators are necessarily
high bandwidth devices in order to obtain good transient response characteristics.
To insure stable closed loop operation, all these devices are frequency compensated, either internally or externally. This compensation can easily be upset by
unwanted stray circuit capacitances and lead inductances, resulting in spurious
oscillations. Therefore, it is important that the circuit lead lengths be short and the
layout as tight as possible. Particular attention should be paid to locating the
compensation and bypass capacitors as close to the IC as possible. Lead lengths
associated with the external pass element(s), if used, should also be minimized.
Often overlooked is the stray inductance associated with the input leads to the
regulator circuit. If the lead length from the input supply filter capacitor to the
regulator input is more than a couple of inches, a O.OI-I.OjLF high frequency type
capacitor (tantalum, ceramic, etc.) should be used to bypass the supply leads close
to the regulator input pins.
A typical good circuit layout is shown in Figure 5-1 for an MC1569R
regulator circuit configuration.
RSC
1
3
+Vin
+Vo
[
I
6
0.01/oL F *'Ci
I
~
9
R1
0.001 /oL F
5
B
1'1 A
>----
-=
C c 02
RC
f---<
J
- /oL F
Case
CNIO""'
R2=6.B k
-=
:f::
7
>--
C
~
4 £
01
MC1569R
MC1469R
I
-=-
CT'
'Ci - May be required if long input leads are used.
Figure 5·1. Typical Regulator Circuit Layout
51
-=
Typical Printed Circuit Board Layout
2"
Location of Components
Vo
J1
Co Gnd
·Ci not shown
Figure 5-1. Typical Regulator Circuit Layout (cont.)
2. Ground Loops and Remote Voltage Sensing
Ground Loops
Regulator performance can also suffer if ground loops in the circuit wiring
are not avoided. The most common ground loop problem occurs when the return
lead of the input supply filter capacitor is improperly located, as shown in Figure
5-2. If this return lead is physically connected between the load return and the
regulator circuit ground point ("B"), a ripple voltage component (60 or 120 Hz)
can be induced on the load voltage, VL. This is due to the high peaks of the filter
capacitor ripple current, hipple, flowing through the lead resistance between the
load and regulator. These peaks can be 5 to 15 times the value of load current.
Since the regulator will only keep constant the voltage between its sense lead and
ground point, points "A" and "B" in Figure 5-2, this additional ripple voltage,
VLEAD, will appear at the load.
This problem can be avoided by proper placement and connection of the
filter capacitor return load as shown in Figure 5-3.
52
WRONG!
Regu lator
Circuit
"A"
~
VOUT
to
XFMR
Figure 5·2. Filter Capacitor Ground Loop
RIGHT!
Regulator
Circuit
+
C
"8"
to
XFMR
irlppl e
Figure 5·3.
53
itA"
AUT
Remote Voltage Sensing
Closely related to the above ground loop problem, is resistance in the current
carrying leads to the load. This can cause poorer than expected load regulation
in cases where the load currents are large or where the load is located some
distance from the regulator. This is illustrated in Figure 5-4. As stated previously,
the regulator circuit will keep the voltage present between its sense and ground
pins constant. From Figure 5-4 we can see that any lead resistance between these
points and the load will cause the load voltage, VL, to vary with varying load
current, iL. This effectively lowers the load regulation of the circuit.
r - - - - - - - , Output
Regulator
Circuit
Sense
+
Gnd
Figure 5-4. Effects of Resistance in Output Leads
u pu
O
tt
DRegulator
Circuit
r<>
~A
v
v
"
se';;'se
==
v{
+
OGnd
A
'V'
Figure 5-5. Remote Voltage Sensing
This problem can be avoided by use of remote sense leads, as shown in
Figure 5-5. The voltage drops in the high current carrying leads now have no
effect on the load voltage, VL. However, since the sense and ground leads are
usually rather long, care must be exercised that their associated lead inductance
is minimized, or loop instability may result. The ground and sense leads should
be formed into a twisted pair lead to minimize their lead inductance and noise
pickup.
54
3. Semiconductor Mounting Considerations
An area of regulator construction which frequently does not receive proper
attention is the mounting of the semiconductor power devices. Improper mounting
of the external series pass transistor(s) and/or IC regulator, if in a power type
package (TO-3, TO-66, TO-220, etc.), can result in higher than expected case
to heatsink thermal resistances (for thermal information see Section 15) or worse,
mechanical damage to the package.
Most problems associated with mounting can be avoided if the following rules
are observed:
1. The mounting surface should be flat, smooth, free of deep scratches or burrs,
and free of paint, varnish, anodization, or oxidation.
2. Always use a thermal joint compound at the mounting interface (Dow-Coming
340, etc.)
3. Mounting holes should be no larger than those on the semiconductor package;
and should be free of burrs or chamfers.
4. TO-3 and TO-66 style packages£can be torqued down to the torque limit of the
mounting hardware.
Examples of TO-3/TO-66 and TO-220 (Case 221A) mounting techniques
are shown in Figures 5-6 and 5-7, respectively.
Sheet Metal
Screws
Clearance
Holes
Clearance
Holes
Thermal
Grease
Applied
Here
Screws or Rivets
Figure 5-6. Mounting Details for Flat-Base Mounted Semiconductors (TO-66 Shown). When not
using a socket, machine screws tightened to their torque limits will produce lowest thermal
resistance.
55
PREFERRED ARRANGEMENT
for Isolated or Non.isolated
Mounting. Screw is at Semi·
conductor Case Potential.
6·32 Hardware is Used.
TO-220
ALTERNATE ARRANGEMENT
for Isolated Mounting
when Screw must be at
Heat-Sink Potential.
4-40 Hardware is Used.
Choose from Parts Listed
Below.
Use Parts Listed Below.
...
...
6-32 HEX HEAD SCREW
B09489A035
/T~4-40
L,,J
(1) RECTANGULAR STEEL~
WASHER
B09002A001
I:
1
HEX HEAD SCREW
B09489A034
1-- NYLON INSULATING BUSHING
B51547F015
SEMICONDUCTOR
(CASE 221, 221A)
(2) RECTANGULAR MICA
INSULA TOR
""
>
\.----JL..----,-_--'-_ _ _ _ _ _- - - - '
B08853A001
""
HEAT SINK -
~S'-___-'I
I
I'-___---'~<"
,...-~-~-,
(2) NYLON BUSHING - - - _ }
B51547F005
:
:
'---..
I
RECTANGULAR
MICA INSULATOR
'---..
'-C_---'-:-;--L-:_-'~
B08853AOOl
HEAT SINK
(3) FLAT WASHER - - - ==~==::>
B51567F036
_ _ COMPRESSION WASHER
(4) COMPRESSION or _----\'----'-;--"--_(
LOCK WASHER
B52200F004
____
TORQUE
REQUIREMENTS
Insulated
0.68 N-M (6 in-Ibs) max
Noninsulated
(I
-
6-32 HEX NUT
B09490AOO6
(1)
(2)
(3)
(4)
I
-~
X )_---
1
B52200F005
4-40 HEX NUT
B09490A005
Used with thin chassis and/or large hole.
Used when isolation is required.
Required when nylon bushing and lock washer are used.
Compression washer preferred when plastic insulating
material is used.
0.9 N-M (8 in-Ibs) max
Figure 5-7. Mounting Scheme for the TO-220 (Case 221A)
56
SECTION 6
LINEAR REGULATOR DESIGN EXAMPLE
As an illustration of the use of the material contained in the preceeding
sections, the following regulator design example is given.
Regulator Performance Requirements
Output Voltage, Vo = + lOV ± .1 V
Output Current, 10 = lA, current limited
Load Regulation, ~ .1% for 10 = lOrnA to 750mA
Line Regulation, ~ .1 %
Output ripple, ~ 2m V p-p
Max Ambient Temperature, TA ~ + 70°C
Supply will have common loads to a negative supply
1. IC Regulator Selection: Study ofthe available regulators given in the selection
guide of Section 17 reveals that both the MCl723C and MC1469 would meet the
regulation performance requirements. Both regulators must be current boosted
to obtain the required 1A output current A rough cost estimate shows that an
MCl723C1 series pass element combination is the most economical approach.
2. Circuit Configuration: In Section 3, an appropriate circuit configuration is
found. This is the MCl723 NPN boost configuration of Figure 3-5A.
3. Determination of Component Values: Using the equations given in Figure
3-5A, the values of CREF, R1, R2, R3 and Rsc are determined:
a. CREF is chosen to be O.If.LF for low noise operation.
b. Rl + R2 is chosen to be = 10K.
c. R2 is then given by: R2
= ~: (Rl + R2) =
.7 (10K) = 7K
d. Since VREF can vary by as much as ± 5% for the MCI723C, R2 should be made
variable by at least that much, so that Vo can be set to the required value of + 10V ±
. 1V. R2 is therefore chosen to consist of a 62K resistor and a 2K trimpot.
e. Rl = 10K - R2 = 10K - 7K = 3K
f. Rsc
= °i~cV = °i~V = .60; .560, lW chosen for Rsc.
g. R3 = RIll R2
=::
2. 2K
4. Determination of Input Voltage, VIN: There are two basic constraints on the
input voltage: (1) the device limits for minimum and maximum VIN and (2) the
minimum input-output voltage differential. These limits are found on the device
data sheet (Section 18.) to be:
57
9.SV :::; VIN :::; 40V and (VIN - Va) ;::,: 3V
For the configuration of Figure 3-SA, (VIN - Yo) is given by:
=
(VIN - Va)
[VIN - (Va + 2cp)] ;::,: 3V where (/p
=
YBEON
= 0.6V
Note that (VIN - Va) is defined on the device data sheet to be the differential
between the input and output pins. Since the base-emitter junction drops of Q1 and
Rsc have been added to the circuit, they must be added to the minimum value of
(VIN - Va). Therefore,
VIN ;::,: VA + 2cp t 3V = 10 + 1.2 + 3
VIN;::': 14.2V
This condition also satisfies the requirement for a minimum VIN of 9.SV.
b. In order to simplify the design of the input supply (see Section 8), VIN is
chosen to be 16V average with a 3V POp ripple at full load and up to 2SV at no
load. This assures that the input voltage is always above the required minimum
value of 14.2Y. Now, the output ripple can be determined. The MCl723C has
a typical ripple rejection ratio of -74 db, as given on its data sheet. With an
input ripple of 3V pop, the output ripple would be less than 1m V Pop, which
meets the regulator output ripple requirements,
S. Determination of regulator package and available output current: Referring to the MC 1723 data sheet (Section 18), there are two package styles to
choose from. Since the two packages have different thermal characteristics, the
amount of available output current will be different for each.
This can be found from:
n = TA + ()JA PD (Eq. 6.1 from Section IS)
where
()JA = heatsink and/or pkg total junction-to-ambient thermal
resistance
PD = VIN x (10
+
lIB)
lIB = quiescent current of IC regulator
10 = IC regulator output current
solving for 10:
10 =
l
(TJ - TA)]
()JA VIN
- lIB
(6.1)
From the device data sheet, we can find the values of n, ()JA, and lIB. Eq 6.1
can then be solved. The results are summarized below for an unheatsinked
MC 1723CL (ceramic DIP), an unheatsinked MC 1723CG (metal can), and an
infinitely heatsinked MC 1723CG packages.
TABLE 6-1
MC1723CL
MC1723CG
MC1723CG
Heatsink
None
None
Infinite
TJ
TA
OJA
liB
175°C
70°C
150°C/W
4mA
150°C
70°C
184°C/W
4mA
150°C
70°C
70°C/W
4mA
10
40mA
23m A
67mA
58
A choice must now be made. Since it is desirable to have as much available current
as possible to drive Q1 (thereby lowering its gain (hfe) requirements), an infinitely
heats inked MC 1723CG is the most desirable choice. However, the construction of
an infinite heats ink is hardly practical. Therefore, the choice is between an unheatsinked MCl723CL and an MCl723CG with some form of heatsinking. The
unheatsinked MCl723CL is chosen since this approach is the least complex.
6. Selection of the Series Pass Element, Ql: The transistor type chosen for Q1
must have the following characteristics (see Section 4):
~
a. VCEO
b. ICMAX
c. hfe
~
~
VINMAX
Isc
Isc @
To
VCE = VIN - Va - if>
if> = VBEON = 0.6V
where
d. PDMAX ~ VIN,
X
Isc
e. (hc such to allow practical heatsinking
f. SOA such that it can withstand
VCE = VIN @ Ie = Isc
for this example:
VCEO
~
25V
ICMAx
~
1A
hfe ~ 25 @ VCE
PDMAX
~
=
5V @ Ie
=
1A
16W
(hc = 1.52°C/W
SOA:
1A @ 16V
A 2N3055 transistor is chosen as a suitable device for Q 1 using the selection
guide of Section 4 and the transistor data sheets (available from device
manufacturer) .
7. Ql Heatsink Calculation
where
TJ = TA
+
PD = VIN
X
(}JA PD (Eq 15.1 from Section 15)
Isc
(hA = (hc + (}cs + OSA (Eq 6.2)
solving for OSA:
- TAl - (OlC + Ocs)
OSA = [ Tl PD
(6.2)
From the 2N3055 data sheet, TJ = 200°C and OJe = 1.52°ClW. The transistor
will be mounted with thermal grease directly to the heatsink. Therefore, (Jcs is
found to be 0.1 °c/W from Table 15-1.
Solving 6.2:
59
(}SA
=
[20?;~ ~ irC] ~
(1.52 +0.1) °C/W
6.6°C/W
A commercial heatsink is now chosen from Table 15-2 or a custom designed
using the methods given in Section 15. For this example, a thermalloy 6003
heatsink having a ()CS of 6.2°C/W was used.
8. Clamp Diode: Since the regulator can power a load which is also connected to a
negative supply, a IN4001 diode is connected to the output for protection. (See
general design considerations, Section 3H.) The complete circuit schematic is
shown in Figure 6-1.
2N3055 on
Thermalloy #6003
0.56, 1W
~~~~~~-'---UVo=
+10 V,
Q1
10
1 A
--""
2
MC1723CL
3
4
13
7
100pf
Figure 6-1. +10V, 1A Design Example
9. Construction Input Supply Design: The input supply is now designed using
the information contained in Section 8 and the regulator circuit is constructed
using the guidelines given in Section 5.
60
SECTION 7
LINEAR REGULATOR CIRCUIT
TROUBLESHOOTING CHECKLIST
Occasionally the designer's prototype regulator circuit will not operate properly. If problems do occur, the trouble can be traced to a design error in 99.9% of the
cases. As a troubleshooting aid to the designer, the following guide is presented.
Of course, it would be difficult, if not impossible, to devise a troubleshooting
guide which would cover all possible situations. However, the checklist provided
will help the designer pinpoint the problem in the majority of cases. To use the
guide, first locate the problem's symptom(s) and then carefully recheck the regulator design in the area indicated using the information contained in the referenced
handbook section.
SYMPTOM
Regulator Oscillates
DESIGN AREA TO CHECK
1. Layout
2. Compensation capacitor too small
3. Input leads not bypassed
4. External pass element parasitically
REFER TO
SECTION
5
3, 18
5
5
oscillating
Loss of Regulation at
Light Loads
Loss of Regulation at
Heavy Loads
IC Regulator or Pass
Element Fails after
Warm-Up or at High
TA
Pass Element Fails
During Short Circuit
1. Emitter-Base resistor in "PNP"
type boost configuration too large
2. Absence of 1 rnA "minimum" load
(see load regulation test spec on
device data sheet)
3. Improper circuit configuration
1. Input Voltage too low (VINMIN,
IVIN - VoIMIN)
2. External pass element gain too low
3. Current limit too low
4. Line resistance between sense points
and load
5. Inadequate heatsinking
4
18
3
2, 3, 18
17
4
3
5
15
15
1. Inaequate heats inking
2. Input Voltage Transient (VINMAX, 2,4,5,17,18
VCEO)
1. Insufficient pass element ratings
(SOA, IcMAX)
2. Inadequate heats inking
61
4
15
TROUBLESHOOTING CHECKLIST
SYMPTOM
IC Regulator Fails
During Short Circuit
1. IC current or SOA capability
exceeded
2. Inadequate heatsinking
IC Regulator Fails
During Power Up
1. Input voltage transient (VINMAX)
2. IC current or SOA capability
exceeded as load (capacitor)
charged up.
IC Regulator Fails
During Power-Down
REFER TO
SECTION
2, 18
DESIGN AREA TO CHECK
2, 18
2, 18
IS
1. Regulator reverse biased
Output Voltage Does 1. Output polarity reversal
Not Come Up During 2. Load has "latched-up" in some
Power-Up or After
manner (usually seen with op amps,
Short Circuit
current sources, etc.)
Excessive 60 or 120
Hz Output Ripple
1. Input supply filter capacitor ground
loop
3.H
3.H
5
If, after carefully rechecking the circuit, the designer is not successful in
resolving the problem, seek assistance from the factory by contacting the nearest
Motorola Sales office.
62
SECTION 8
DESIGNING THE INPUT SUPPLY
Most input supplies used to power series pass regulator circuits consist of
a 60 Hz, single phase step-down transformer followed by a rectifier circuit whose
output is smoothed by a choke or capacitor input filter. The type of rectifier circuit
used can be either a half-wave, full-wave, or full-wave bridge type, as shown
in Figure 8-1. The half-wave circuit is used in low current applications, while
the full-wave is preferrable in high-current, low output voltage cases. The fullwave bridge is usually used in all other high-current applications.
Half-Wave
Full-Wave or Full-Wave Center Tap
FUll-Wave Bridge
Figure 8-1. Rectification Schemes
63
In this section, specification of the filter capacitor, rectifier and transformer
ratings will be discussed. The specifications for the choke input filter will not be
considered since the simpler capacitor input type is more commonly used in series
regulated circuits. A detailed description of this type of filter can be found in the
reference listed at the end of this section.
1. Design of Capacitor-Input Filters
The best practical procedure for the design of capacitor-input filters still
remains based on the graphical data presented by Schadel in 1943. The curves
shown in Figures 8-2 through 8-5 give all the required design information for
half-wave and full-wave rectifier circuits. Whereas Schade originally also gave
curves for the impedance of vacuum-tube rectifiers, the equivalent values for
semiconductor diodes must be substituted. However, the rectifier forward drop
often assumes more significance than the dynamic resistance in low-voltage supply
applications, as the dynamic resistance can generally be neglected when compared
with the sum of the transformer secondary-winding resistance plus the reflected
primary-winding resistance. The forward drop may be of considerable importance,
however, since it is about 1 V, which clearly cannot be ignored in supplies of 12 V
or less.
)0
v~
90
RS
N
~
L~
~'ctDR'
~
yy
V
~r--
2
V
4
r:
70
60
I-
6
t-"
8
o
2.5
15
......
t-"
50
30
25
30
35
40
50
60
70
{/II
40
~ ~F=
20
0.05
0.5
t%v
~~~
~~
r:::---
80
90
100
10
0
0.1
10
100
1,000
wCR L (C in farads, R L in ohms)
w = 21Tf, f = line frequency
Figure 8-2. Relation of applied alternating peak voltage to direct output voltage In halfwave capacitor-Input circuits. (From O. H. Schade, Proc. IRE, vol. 31, p. 356,
1943.)
64
005
0.1
0.5
100
90
80
70
VC(DC)%
VM
60
50
40
]~~~ IfF
Bridge
~'w~.
~~
~~
i.oIII
~~
1
2
v ...v
~
~~
4
6
8
f.-r-
IIi;'
~~
1o
1 2.5
15
r-
~ VVI-'
V
20
~ r:::1;
30
35
40
V lV
I-- I--
50
60
70
80
90
I;
~ VI;
.....r-
r-
l --- r-
30
0.1
~(%)
RL
25
00
10
wC R L (C in farads, R L in ohms)
1,000
100
w~21Tf, f~line
frequency
Figure 8-3, Relation of applied alternating peak voltage to direct output voltage in fullwave capacitor-input circuits. (From O. H. Schade, Proc. IRE, vol. 31, p. 356, 1943.)
65
'i 10
"0
.!! 7
.
c
CD
0.02
0.05
...
0.1
0.2 I[
c:
0.5 .....
0.1
0.2 1["'
0.5
10
30
100
5
!!:.
>
~ 10
70 100
200 300
~
I~
f--
::::
0.02
...-
0.05
-
0.1
0.2
~
7
Vin
+ Vin
0------/
- Vout
C. Boost variation which
resembles the flyback
regulator (step up or
down)
Figure 10-2. Non-Isolated DC-DC Converters
79
For both regulators, transient response or responses to step changes in load
are very difficult to analyze. They lead to what is termed a "load dump" problem.
This requires that energy already stored in the choke or filter be provided with
a place to go when load is abruptly removed. Practical solutions to this problem
include limiting the minimum load and using the right amount of filter capacitance
to give the regulator time to respond to this change.
B. FLYBACK AND FORWARD CONVERTERS
To take advantage of the regulating techniques just discussed, and also
provide isolation, a total of five popular topologies have evolved and are illustrated
in figures 10-3 and 10-6. Each circuit has a practical power range or capability
associated with it as follows:
Circuit
Flyback
Power Range
50 to 100 watts
Motorola Reference
EB87
Forward
100 to 200 watts
Power Leader
Push-Pull
200 to 500 watts
EB88, AN-737A
Half Bridge
200 to 500 watts
EB's 86 & 100, AN-767
Full Bridge
500 to 2000 watts
EB-85
First to be discussed will be the low power (20-200 W) converters which
are dominated by the single transistor circuits shown in Figure 10-3. All of these
circuits operate the magnetic element in the unipolar rather than bipolar mode.
This means that transformer size is sacrificed for circuit simplicity.
1. Flyback - The flyback (alternately known as the "ringing choke") regulator
stores energy in the primary winding and dumps it into the secondary windings
(Figure 1O-3A). A clamp winding is usually present to allow energy stored in the
leakage reactance to return safely to the line instead of avalanching the switching
transistor. The operating model for this circuit is the boost circuit variation discussed earlier. The flyback is the lowest cost regulator (except at high power
levels) because output filter chokes are not required, since the output capacitors
feed from a current source rather than a voltage source. Because of this, the
flyback will have higher output ripple than the forward converter. However, the
ftyback is an excellent choice when multiple output voltages are required and
does tend to provide better cross regulation than the other types. In other words,
changing the load on one winding will have little effect on the output voltage of
the others.
A 120/220 Vac flyback design requires transistors that block twice the peak
line plus transients or about 1.0 kYo Presently, variations of 1200 to 1500 V
horizontal deflection transistors are used here. These bipolar devices are relatively
slow (t[ = 200-500 ns) and tend to limit efficient operating frequencies to 20-40
kHz. Introduction of 1000 V TMOS FET will soon permit operation at much
higher frequencies. Faster 1.0 kV bipolar transistors are also anticipated in the
near future and will provide a lower cost alternative. The two transistor variation
of this circuit (Figure 10-3C) eliminates the clamp winding and adds
80
10-3A. Flyback
(Clamp Winding
Is Optional)
10-3B. Forward
(Clamp Winding
Is Necessary)
10-3C. Two Transistor
Forward or
Flyback (Clamp
Winding Is Not
Needed)
Figure 10-3. Low Power Popular (20-200 W) Converter Topologies
81
a transistor and diode to effectively clamp peak transistor voltages to the line.
With this circuit a designer can safely use the faster 400 V to 500 V bipolar or
FET Switchmode transistors and push operating frequencies considerably higher.
There is a cost penalty here over the single transistor circuit due to the extra
transistor, diode and floating base drive requirement of the upper switch transistor.
A subtle variation in the method of operation can be applied to either of
these circuits. The difference is referred to as operation in the discontinuous or
continuous mode, and the waveform diagrams are shown in Figure 10-4. The
analysis given in the earlier section on boost regulators dealt strictly with the
discontinuous mode where all the energy is dumped from the choke before the
transistor turns on again. If the transistor is turned on while energy is still being
dumped into the load, the circuit is operating in the continuous mode. This is
generally an advantage for the transistor in that it needs to switch only half as
much peak current in order to deliver the same power to the load. In many
instances, the same transformer may be used with only the gap reduced to provide
more inductance. Sometimes the core size will need to be increased to support
the higher LI product (2 to 4 times) now required, because the inductance must
increase by almost 10 times to effectively reduce the peak current by two. In
dealing with the continuous mode, it should also be noted that the transistor must
now tum-on from 500 to 600 V rather than 400 V level, because there no longer
is any dead time to allow the flyback voltage to settle back down to the input
voltage level. Generally it is advisable to have VCEO (sus) ratings comparable to
the tum-on requirements.
The flyback converter stands out from the others in its need for a low
inductance, high current primary. Conventional E and pot core ferrites are difficult
to work with because their permeability is too high even with relatively large
gaps (50 to 100 mili-inches). The industry needs something better (like powered
iron) that will provide permeabilities of 60 to 120 instead of 2000 to 3000 for
this application.
800 V
VCE
VCE
-400 V
OV
2.0A
1.0 A
OA
Discontinuous Mode
Continuous Mode
Figure 10-4. Flyback Transistor Waveforms
82
- - BOOV
-
'--
'--
- - 400 V
- - OV
--
1.0A
--
OA
Figure 10-5. Forward Converter Transistor Waveforms
2. Forward - The single transistor forward converter is shown in Figure
1O-3B. Although it initially appears very similar to the flyback, it is not. The
operating model for this circuit is actually the buck regulator discussed earlier.
Instead of storing energy in the transformer and then delivering it to the load,
this circuit uses the transformer in the active or forward mode and delivers power
to the load while the transistor is on. The additional output rectifier is used as
a freewheeling diode from the LC filter, and the third winding is actually a reset
winding. It generally has the same turns as the primary (is usually bifilar wound)
and clamps the reset voltage to twice the line. However, its main function is to
return energy stored in the magnetizing inductance to the line and thereby reset
the core after each cycle of operation. Because it takes the same time to set and
reset the core, the duty cycle of this circuit cannot exceed 50%. This also is a
very popular low power converter, and like the flyback, is practically immune
from transformer saturation problems. Transistor waveforms shown in Figure 105 illustrate that the voltage requirements are identical to the flyback. For the single
transistor versions, 400 V tum-on and 1.0 kV blocking devices like the 1200 to
1500 V deflection transistors are required. The two transistor circuit variation
shown in Figure 1O-3C again adds a cost penalty, but allows a designer to use
the faster 400 to 500 V devices. With this circuit, operation in the discontinuous
mode refers to the time when the load is reduced to a point where the filter choke
runs "dry." This means that choke current starts at and returns to zero during
each cycle of operation. Even though there are no adverse effects on the components themselves, most designers prefer to avoid this type of mode because of
higher ripple and noise. Standard ferrite cores work fine here and in the high
power converters as well. In these applications, no gap is used as the high
permeability (3000) results in a desirable effect of very low magnetizing current
levels.
83
C. PUSH-PULL AND BRIDGE CONVERTERS
The high power circuits shown in Figure 10-6 all operate the magnetic
element in the bipolar or push-pull mode and require 2 to 4 inverter transistors.
Because the transformers operate in this mode, they tend to be almost half the
size of the equivalent single transistor converters and thereby provide a cost
advantage over their counterparts at power levels of 100 watts to 1.0 kW.
1. Push-Pull - The push-pull converter shown in Figure 1O-6A is one of the
oldest converter circuits around. Its early use was in low voltage inverters such
as the 12 Vdc to 120 Vdc power source for recreational vehicles and in dc to dc
converters. Because these converters are free running rather than driven and
operate from low voltages, transformer saturation problems are minimal. In the
high voltage off line switchers, saturation problems are common and difficult to"
solve. The transistors are also subjected to twice the peak line voltage which
requires the use of relatively slow 1.0 kV transistors. Both of these drawbacks
have tended to discourage designers of off line switchers from using this topology.
2. Half and Full Bridge - The most popular high power converter today is the
half bridge (Figure 1O-6B). It has two clear advantages over the push-pull type.
First, the transistors never see more than the peak line voltage and standard 400
V fast Switchmode transistors that are now readily available may be used. Second,
and probably even more important, transformer saturation problems are easily
minimized by use of a small coupling capacitor (2.0 IJ-F "'" Cc "'" 5.0 IJ-F) as
shown. Because the primary winding is driven in both directions, a full wave
output filter, rather than half, is now used, and the core is actually utilized more
effectively. Another more subtle advantage of this circuit is that the input filter
capacitors are placed in series across the rectified 220 Vac line which allows them
to be used as the voltage doubler elements on a 120 Vac line. This allows the
inverter transformer to operate from a nominal 320 Vdc bus when the circuit is
connected to either 120 Vac or 220 Vac. Finally, this topology allows diode
clamps across each transistor to contain destructive switching transients. The
designers dream, of course, is for fast transistors that can handle a clamped
inductive load line at rated current. And a few (like the Switchmode III and
TMOS FET series from Motorola) are beginning to appear on the market. However, the older designs in this area stilI end up using snubbers to protect the
transistor which sacrifices both cost and efficiency.
The effective current limit of today's low cost TO-3 transistors (300 mil die)
is somewhere in the 10 to 20 A area. Once this limit is reached, the designer
generally changes to the full bridge topology shown in Figure 1O-6C. Because
full line rather than half is applied to the primary winding, the power output can
almost double that of the half bridge with the same switching transistors.
Another variation of the half bridge is the split winding circuit shown in
Figure 10-60. A diode clamp can protect the lower transistor but a snubber or
zener clamp must stilI be used to protect the top transistor from switching transients. Because both emitters are at an ac ground point, expensive drive transformers can now be replaced by lower cost capacitively coupled drive circuits.
84
L....._-o +Vout
A. Push Pull
+ Vin o--__--~
+Vout
B. Half Bridge
L.....,_ _--
Ol
'E0
0
""
.0
'>-"
0
0:::
.s
......-
-
=
-
~
V
'O\\~
/
~
v
??..~
V
--
~ """"
........, I--"'"
?.'O\~
~/
~
,.-
~C~<:>
~
--
~
?;,O\9'?
:;....---......
_.....
-
-:::;;-
~
~
~Cb"\
-~
50
---::::: ~
;.....-
~~
~
-
--
E.C~-
-
-----
.......
~
----
'-"
.0
(f)
Q)
<0
'~"
0
Q)
"Ol
.s
2
'6
c:
'"(;;
.<::
;:
0
a..
-
-
Q;
1 -
-0
z
I
L--
.
10
20
30
40
50
Figure 11 1 Core Selection for Bridge Configurations Compliments of Ferroxcube
88
-
Finally, once a mechanical fit has been obtained, it is time for the circuit
tests. The voltage rating is strictly a mechanical problem and is one of the reasons
why U.L. normally does not allow high voltage bifilar windings. The inductance
and saturating current level of the primary are inherent to the design, and should
be checked in the circuit or other suitable test fixture. Such a fixture is shown
in Figure 11-2 where the transistor and diode are sized to handle the anticipated
currents. The pulse generator is run at a low enough duty cycle to allow the core
to reset. Pulse width is increased until the start of saturation is observed (Isat).
Inductance is found using
L = V di
dt
In forward converters, the transformer generally has no gap in order to
minimize the magnetizing current (1M ), For these applications the core should be
chosen to be large enough so that the resulting LI product insures that 1M at
operating voltages is less than Isat . For flyback designs, a gap is necessary and
the test circuit is useful again to evaluate the effect of the gap. The gap will
normally be quite large where:
Lm/f..L
gap length
magnetic path length
f..L=
permeability
Under this stipulation, the gap directly controls the LI parameters. Doubling
it will decrease L by two and increase Isat by two. Again, the anticipated switching
currents must be less than Isat when the core is gapped to ensure correct inductance.
Transformer tests in the actual supply are usually done with a high voltage
dc power supply on the primary and with a pulse generator or other manual
control for the pulse width drive such as using the control Ie in an open loop
configuration.
+20 V
TIME
L
=
V Ale
At
Figure 11-2. Simple Coli Tester
89
•
Here the designer must recheck three areas:
1. No evidence of core saturation
2. Correct amount of secondary voltage
3. Minimum core or winding heat rise
If problems are detected in any of these areas, one possible solution is to
redesign using the next larger core size. However, if problems are minimal, or
none exist, it is possible to stay with the same core or even consider using the
next smaller size.
B. TRANSISTORS
The initial selection of a transistor(s) for a switcher is basically a problem
of finding the one with voltage and current capabilities that are compatible with
the application. For the final choice, performance and cost tradeoffs among devices from the same or several manufacturers have to be weighed. Before these
devices can be put in the circuit, both protective and drive circuits will have to
be designed.
Motorola's first line of devices for switchers were trademarked "Switchmode" transistors and introduced in the early 70's. Data sheets were provided
with all the information that a designer would need, including reverse bias safe
operating area (RBSOA) and performance at elevated temperature (l00°C). The
first series was the 2N6542 through 6547, TO-3 devices which were followed by
the MJE13004 series in a plastic TO-220 package. Finally, high voltage (1.0 kV)
requirements were met by the metal MJl2002 and MJ8500 series and the plastic
MJEI2007. Just recently, Motorola introduced three new families of "Switchmode" transistors shown in Table 11-2. The Switchmode II series is basically
a faster switching version of Switchmode I. Switchmode III is the Cadillac of
today's industry with both exceptional speed and RBSOA. Here, device cost is
up but system costs may be lowered because of reduced snubber requirements
and higher operating frequencies. A similar argument applies to Motorola T-MOS
PET's. These devices make it possible to switch efficiently at higher frequencies
(200 to 500 kHz), but the main selling point is that they are easier to drive. This
latter point is the one most often made to show that systems savings are again
quite possible even though the initial device cost is higher.
TABLE 11-2
Motorola High Voltage Switching Transistor Technologies
Family
SWITCHMODE I
Typical
Device
Typical Fall
Time
Approximate
Switching
Frequency
2N6545
MJE13005
MJE12007
200-500 ns
20K
SWITCH MODE II
MJ12010
100 ns
100K
SWITCHMODE III
MJ13010
50 ns
200K
T-FET'S
MTP565
20 ns
500K
90
TABLE 11·3
Power Transistor Voltage Chart
Circuit
Line
Voltage
220
120
Flyback, Forward or
Push·Pull
Half or Full Bridge
VCEV
VCEO(sus)
VCEO(sus)
VCEV
850
450
400
200
400
200
400
200
Table 11-3 is a review of the transistor voltage requirements for the various
off line converter circuits. As illustrated, the most stringent requirement for single
transistor circuits (ftyback and forward) is the blocking or VCEV t:ating. Bridge
circuits, on the other hand, tum on and off from the dc bus and their most critical
voltage is the tum on or VCEO (sus) rating. To help designers select parts for these
applications, Motorola has provided the selection charts in Appendix A. Each
table lists devices that are appropriate for a given line voltage and circuit configuration and various power handling capabilities. Table 1 contains devices listed
by their current (power handling) rating and 200 < VCEO < 400 V for use in 120
Vac bridge circuits. Tables 2 and 3 list the remaining devices (V CEO ~ 400 V)
which would be appropriate for 220 Vac and 380 Vac bridge circuits. Tables 4
and 5 list devices by their VCEV rating. These tables can therefore be used to
select devices for either 120 or 220 Vac single transistor circuits (ftyback and
forward converters).
R
c
Figure 11·3. Zener Clamp and Snubber for Single Transistor Converters
91
Most Switchmode transistor load lines are inductive during tum on and tum
off. Tum on is generally inductive because the short circuit created by output
rectifier reverse recovery times is isolated by leakage inductance in the transformer. This inductance effectively snubs most tum-on load lines so that the
rectifier recovery (or short circuit) current and the input voltage are not applied
simultaneously to the transistor. Sometimes primary interwinding capacitance
presents a small current spike, but usually tum-on transients are not a problem.
Tum-off transients due to this same leakage inductance, however, are almost
always a problem. In bridge circuits, clamp diodes can be used to limit these
voltage spikes. If the resulting inductive load line exceeds the transistor's reverse
bias switching capability (RBSOA) then an RC network may also be added across
the primary to absorb some of this transient energy. The time constant of this
network should equal the anticipated switching time of the transistor (100 ns to
1 J.Ls). Resistance values of 100 to 1000 ohms in this RC network are generally
appropriate. Trial and error will indicate how low the resistor has to be to provide
the correct amount of snubbing. For single transistor converters, the snubber
shown in Figure 11-3 is generally used. Here slightly different criteria are used
to define the R and C values:
C=
where
~
y
I =
The peak switching current
tf =
The transistor fall time
y=
The peak switching voltage
(Approximately twice the dc bus)
also
R=
toniC (it is not necessary to completely discharge this capacitor to obtain the desired
effects of this circuit)
where
ton =
The minimum on time or pulse width
and
PR =
--
Cy2f
2
where
and
PR =
f=
The power rating of the resistor
The operating frequency
Most of today's transistors that are used in 20 kHz converters switch slow enough
so that most of the energy stored in the leakage inductance is dissipated by the
snubber or transistor, causing very little voltage overshoot. Higher speed converters and transistors present a slightly different problem. In these newer designs,
snubber elements are smaller and voltage spikes from energy left in the leakage
inductance may be a more critical problem depending on how good the coupling
is between the primary and clamp windings. If necessary, protection from these
spikes may be obtained by adding a zener and rectifier across the primary as
shown in Figure 11-3. Motorola's 1.0 Wand 5.0 W zener devices with ratings
92
up to 200 V can provide the clamping or spike limiting function. If the zener
must handle most of the power, its size can be estimated using:
Pz
LL Ff
2
where
The zener power rating
and
The leakage inductance
(measured with the clamp winding or
secondary shorted)
There are probably as many base drive circuits for bipolars as there are
designers. Ideally, the transistor should have just enough forward drive (current)
to stay in or near saturation and reverse drive that varies with the amount of
•
II
A. Fixed Drive, Turn Off
Energy Stored in Transformer
B. Fixed Drive, Turn Off
Energy Stored in Capacitor
C. Standard Baker Clamp
D. Active Baker Clamp
E. Proportional Base Drive
Figure 11·4. Typical Bipolar Base Drive Circuits
93
stored base charge such as a low impedance reverse voltage. Many of today's
common drive circuits are shown in Figure 11-4. The fixed drive circuits of 114A and 11-4B tend to emphasize economy, while the Baker clamp and proportional
drive circuits of 11-4C, 11-40 and 11-4E emphasize performance over cost.
+ 12 V
r-----,
l---l
COG - .
I
I
1:3
Wave Forms
+15 V
--OV
-15 V
50% Duty Cycle
20% Duty Cycle
VGS Wave Forms
Figure 11-5A. Typical Transformer Coupled FET Drive
'7~-~
v:/
CDG..L
Drive
Circuit
T
1
r
~
I
I
I
I
I
I
I
CGSJ..
500pJ
1. Miller Current for 30 ns
'M = COG dv/dt
300 V
= 100 pF x - - = 1.0 A
30 ns
~
IG
+ 1M
-
2. Gate Cap Current for 30 I')S
IG = CGS dv/dt
6.0 V
= 500 pFx - - = O.lA
30 ns
i
Figure 11-58. FET Drive Current Requirements
94
--10V
--B.OV
h
--2.0 V
I
I
I
I
I
I
I
_
OV
--1.0 A
OA
--1.0A
PET drive circuits are just beginning to appear. The standard that has evolved
at this time is shown in Figure II-5A. This transformer coupled circuit will
produce forward and reverse voltages applied to the FET gate which vary with
the duty cycle as shown. For this example, a VGS rating of 20 V would be
adequate for one condition, but not the other. Higher VGS ratings would solve
the problem, but at this time it is advisable to use a regulated logic supply and
provide only the minimum gate drive required for these situations. Finally, there
is one point that is not 9bvious when looking at the circuit. It turns out that FET's
can be directly coupled to many IC's with only to 100 rnA of sink and source
output capability and still switch efficiently at 20 kHz. However, to switch efficiently at higher frequencies, several amperes of drive may be required on a
pulsed basis in order to quickly charge and discharge the gate capacitances. A
simple example will serve to illustrate this point and also show that the Miller
effect, produced by COG, is the predominant speed limitation when switching
high voltages (see Figure 11-5B). A FET responds instantaneously to changes
in gate voltage and will begin to conduct when the threshold is reached (V GS
= 2.0 to 3.0 V) and be fully on with VGS = 7.0 to 8.0 V. Gate waveforms will
show a step at a point just above the threshold voltage which varies in duration
depending on the amount of drive current available. The drive current determines
both the rise and fall times for the drain current. To estimate drive current
requirements, two simple calculations with gate capacitances can be made:
1.
CoGdv/dt
and
2.
CGsdv/dt
where
1M is the current required by the Miller effect to charge the drain
to gate capacitance at the rate it is desired to move the drain voltage
(and current). And IG is usually the lesser amount of current required
to charge the gate to source capacitance through the linear region
(2.0 to 8.0 V). As an example, if 30 ns switching times are desired
at 300 V where COG
100 pF and CGS = 500 pF, then
1M =
100 pF x 300 V/30 ns = 1.0 A and
IG =
500 pF x 6.0 V/30 ns = 0.1 A
This example shows the direct proportion of drive current capability to speed.
It also jllustrates that for most devices, COG will have the greatest effect on
switching speed and that CGS is important only in estimating tum on and tum off
delays.
Aside from rather unique drive requirements, a FET is very similar to a
bipolar transistor. Today's 400 V FET's compete with bipolar transistors in many
switching applications. They are faster and easier to drive, but do cost more and
have higher saturation, or more precisely, on voltages. The performance or efficiency tradeoffs are best analyzed using Figure 11-6. Here, typical power losses
for 5.0 A switching transistors versus frequency are shown. The FET and bipolar
losses were calculated at TJ = 100°C rather than 25°C because on resistance and
switching times are highest here, and 100°C is typical of many applications.
These curves are asymptotes of the actual device performance, but are useful in
establishing the "break point" of various devices, which is the point where
c
95
I
100
!Zi
..9.... a.Ul
30
~+
~ §
.... a.
10
*
'Cij
Bipolar
tf = 0.5 ILS v
/'
",/
-'
FET
tf- 5Ons
3
II
I-
lija.
~
1.0
~
1K
10K
100K
Operating Frequency (Hz)
Figure 11-6. TypIcal Switching Losses at 5.0 A and TJ
1M
10M
= 100·C
saturation and switching losses are equal. Since this is as low as 10 kHz for some
bipolars, it is possible that a FET even with high on voltages can be competitive
efficiency-wise at 20 kHz. The faster Switchmode II and III bipolar products fall
somewhere between the curves shown and therefore are more competitive with
FET's at the higher operating frequencies.
C. RECTIFIERS
Once components for the inverter section of a switcher have been chosen,
it is time to determine how to get power into and out of this section. This is
where the all important rectifier comes into play. The input rectifier is generally
a bridge that operates off the ac line and into a capacitive filter. For the output
section, most designers use Schottkys for efficient rectification of the low voltage,
5.0 V output windings, and for the higher voltage (12 to 15 V) outputs, the more
economical fast recovery diodes are used. A guide to Motorola's rectifier products
is given in Appendix B. Here devices that would normally be used in switchers
from 10 to 2000 watts are listed next to circuits in which they would generally
be used.
For the process of choosing an input rectifier, it is useful to visualize the
circuit shown in Figure 11-7. To reduce cost, most earlier approaches of using
choke input filters, soft start relays (Triacs), or SCR's to bypass a large limiting
resistor have been abandoned in favor of using small limiting resistors or NTC
thermistors, and a large bridge. The bridge must be able to withstand the surge
currents that exist from repetitive starts at peak line. The procedure for finding
the right component and checking its fit is as follows:
1.
Choose a rectifier with 2 to 5 times the average 10 required.
2.
Estimate the peak surge current (Ip) and time (t) using:
1 = I.4Vin
p
Rs
Where Yin is The RMS input voltage
Rs = the total limiting resistance, and
C
= the filter capacitance
96
AC
Line
C
Load
Steps:
1. Choose a rectifier with an 10 rating of 2 to 5 times the actual load.
2. Measure or calculate the inrush current at peakiine voltage.
3. Compare to the equivalent diode rating using IFSM and 12YI= K.
4. If line 3 is less than line 2, use a larger rectifier or increase Rs.
Figure 11-7. Choosing Input Rectifiers
3.
Compare this current pulse to the sub cycle surge current rating (Is) of
the diode itself. If the curve of Is versus time is not given on the data
sheet, the approximate value for Is at a particular pulse width (t) may be
calculated knowing:
• IpSM -
• J2
the single cycle (S.3 ms) surge current rating .
Vt =
tional to
K which applies when the thermal response, ret), is proporms). This gives:
Vt (for t-
Control
IC
Opto
Coupler
B. Three Chip System -
Error
Amp
-
Opto Coupler Isolation
Figure 11-9. Control Circuit Topologies
When it is necessary to drive two or more power transistors, drive transformers are a practical interface element and are driven by the conventional dual
channeliC just discussed (Figure 11-9A). In the case of a single transistor converter, however, it is usually more cost effective to directly drive the transistor
from the IC (Figure 11-9B). In this situation, an opto coupler is commonly used
to couple the feedback signal from the output back to the control Ie. And the
error amplifier in this case is nothing more than an op amp, and reference such
as the TL431 from Motorola.
101
102
SECTION 12
THE FUTURE FOR SWITCHING REGULATORS
The future offers a lot of growth potential for switchers in general - and
low power switchers (50-200 watts) in particular. The latter are responding to
the growth in microprocessor-based equipment, as well as computer peripherals.
Today's topologies have already been challenged by the sine wave inverter, which
reduces noise and improves transistor reliability, but results in a cost penalty.
Also, a trend has begun toward higher switching frequencies to further reduce
size and cost. The latest bipolar transistor can operate efficiently up to 100 kHz,
and the FET seems destined to own the 200 to 500 kHz range.
The growth pattern predicted at this time can possibly be impacted by noise
problems. Originally governed only by MIL specs and the VDE in Europe, the
FCC (effective October 1981) has released a set of specifications that apply to
electronic systems which often include switchers (see FCC Class A in Figure
12-1). It seems probable, however, that system engineers or power supply designers will be able to add the necessary line filters and EMI shields without
adding a significant cost.
.9 100 ~------- VDE OS71 Frequency Range - - -......-.-.11
N
1"- VDE OS75 Frequency Range ~
o
~ SO
I
I
N
I
I
:.:.
I
/
FCC Class A
VDE OS71/A,C
......-______
:.:.
/
000
VDEOS75/N
.§:;: 60-
~----~------------
~ ::l.
~=========../'
'E CD
w,:
~N
w~
../' VDE OS71/B
VDE OS75/N12
~ FCCClassB
40
o
LO
20
N
I
o
~
:>::l.
CD
"0
0.01
0.1
1.0
Frequency (MHz)
10
100
Notes: 1. FCC Class A covers commercial, Class B covers residential.
2. Also SCE VDE 0871/0875 for noise and VDE 0730 or UL478 for safety.
Figure 12-1. Noise Limits
103
The most optimistic note concerning switchers is in the components area.
Switching power supply components have actually evolved from components
used in similar applications. And it is very likely that newer and more mature
products specifically for switchers will continue to appear over the next several
years. The ultimate effect of this evolution will be to further simplify and cost
reduce these designs. Because the designer and component manufacturer must
work as a team to bring this about, companies like Motorola that are looking to
the future will continue a dialogue with designers to keep abreast with their
current and future product needs.
104
SECTION 13
SWITCHING REGULATOR DESIGN EXAMPLES
Three switching regulator power supply designs are covered in this section.
Part A describes a 400 W half bridge and a 1000 W full bridge configuration in
which the TL494 control I.e. is utilized. Part B describes a 60 W flyback regulator
where a MC34060 control I.e. is used. All three design examples are off-line
supplies which can operate from either 115 or 230 Vac.
A. A SIMPLIFIED POWER-SUPPLY DESIGN USING
THE TL494 CONTROL CIRCUIT
The TL494 is a fixed-frequency pulse width modulation control circuit,
incorporating the primary building blocks required for the control of a switching
power supply. (See Figure 13-1.) An internal-linear sawtooth oscillator is
frequency-programmable by two external components, RT and CT. The oscillator
frequency is determined by:
Output pulse width modulation is accomplished by comparison of the positive
sawtooth waveform across capacitor CT to either of two control signals. The NOR
Output Mode Control
13
VCC
8
Flip-Flop
Q
,---,-L---'
CK
Dead·Time
Control
0.7 mA
12
Gnd
Error Amplifier
16
7
Feedback/PW.M.
Comparator Input
5.0 V
Figure 13-1. TL494 Block Diagram
105
Capacitor CT
FeedbackJP.w.M. Compo
Dead-Time Compo
Flip-Flop
Clock Input
Flip-Flop
o
Flip-Flop
Q
Output 01
Emitter
Output 02
Emitter
Output Mode
Control
._
Figure 13-2. TL494 Timing Diagram
gates, which drive output transistors Ql and Q2, are enabled only when the flipflop clock-input line is in its low state. This happens only during that portion of
time when the sawtooth voltage is greater than the control signals. Therefore, an
increase in control-signal amplitude causes a corresponding linear decrease of
output pulse width. (Refer to the timing diagram shown in Figure 13-2.)
The control signals are external inputs that can be fed into the dead-time
control (Figure 13-1, Pin 4), the error amplifier inputs (pins 1, 2, 15, 16), or the
feedback input (Pin 3). The dead-time control comparator has an effective
120 mV input offset which limits the minimum output dead time to approximately
the first 4% of the sawtooth-cycle time. This would result in a maximum duty
cycle of 96% with the output mode control (Pin 13) grounded, and 48% with it
connected to the reference line. Additional dead time may be imposed on the
output by setting the dead time-control input to a fixed voltage, ranging between
o to 3.3 V.
The pulse width modulator comparator provides a means for the error amplifiers to adjust the output pulse width from the maximum percent on-time,
established by the dead time control input, down to zero, as the voltage at the
feedback pin varies fromO.5 to 3.5 V. Both error amplifiers have a commonmode input range from - 0.3 V to (Vcc - 2.0 V), and may be used to sense
power-supply output voltage and current. The error-amplifier outputs are active
high and are ORed together at the non-inverting input of the pulse-width modulator
comparator. With this configuration, the amplifier that demands minimum output
on time, dominates control of the loop.
When capacitor CT is discharged, a positive pulse is generated on the output
of the dead-time comparator, which clocks the pulse-steering flip-flop and inhibits
the output transistors, QI and Q2. With the output-mode control connected to
106
the reference line, the pulse-steering flip-flop directs the modulated pulses to each
of the two output transistors alternately for push-pull operation. The output frequency is equal to half that of the oscillator. Output drive can also be taken from
Q I or Q2, when single-ended operation with a maximum on time of less than
50% is required. This is desirable when the output transformer has a ringback
winding with a catch diode used for snubbing. When higher output drive currents
are required for single-ended operation, Q I and Q2 may be connected in parallel,
and the output mode control pin must be tied to ground to disable the flip-flop.
The output frequency will now be equal to that of the oscillator.
The TL494 has an internal 5.0 V reference capable of sourcing up to lOrnA
of load currents for external bias circuits. The reference has an accuracy of ± 5%
over an operating temperature range of 0 to 70°C.
Application of The TL494 in a 400 Wand 1000 Watt Off-Line Power
Supply
A 5 V, 80 A line operated 25 kHz switching power supply, designed around
the TL494, is shown in Figure 13-3, and the performance data is shown in Table
13-1. The explanation of each section of the power supply, which follows, applies
not only to this model but to the higher power (12 V, 84 A) model shown in
Figure 13-4, as well. In comparing the two, note that the 400-watt design is a
half-bridge, while the 1,000 watt is a full bridge. The 1,000 watt power supply
components switching transistors, transformers, and output rectifiers have been
beefed up.
1. AC Input Section
The operating ac line voltage is selectable for a nominal of 115 or 230 volts
by moving the jumper links to their appropriate positions. The input circuit is a
full wave voltage doubler when connected for 115 Vac operation with both halves
of the bridge connected in parallel for added line surge capability. When connected
for 230 Vac operation, the input circuit forms a standard full wave bridge.
The line voltage tolerance for proper operation is - 10, + 20% of nominal.
The ac line inrush current, during power-up, is limited by resistor R1. It is shorted
out of the circuit by triac Q 1, only after capacitors C 1 and C2 are fully charged,
and the high frequency output transformer Tl, commences operation.
2. Power Section
The high frequency output transformer is driven in a half-bridge configuration
by transistors Q3 and Q5. Each transistor is protected from inductive tum-off
voltage transients by an R-C snubber and a fast recovery clamp rectifier. Transistors Q2 and Q4 provide tum-off drive to Q3 and Q5, respectively. In order to
describe the operation of Q2, consider that Q6 and Q3 are turned on. Energy is
coupled from the primary to the secondary of T3, forward biasing the base-emitter
of Q3, and charging C3 through CRl. Resistor R3 provides a dc path for the
'on' drive after C3 is fully charged. Note that the emitter-base of Q2 is reverse
biased during this time. Tum-off drive to Q3 commences during the dead-time
period, when both Q6 and Q7 are off. During this time, capacitor C3 will forward
bias the base-emitter of Q2 through R3 and R2 causing it to tum-on. The baseemitter of Q3 will now be reverse biased by the charge stored in C3 coupled
through the collector-emitter of Q2.
107
TABLE 13-1
400 WaH Switcher Performance Data
Conditions
Test
Input
Output
Results
103.5 to 138 VAC
5 volts and 80 amps
8 mVO.16%
Load Regulation
115 VAC
5 volts, 0 to 80 amps
Output Ripple
115 VAC
5 volts and 80 amps
20 mV 0.4%
P.A.R.D. 50 mV pop
Efficiency
115 VAC
5 volts and 80 amps
73%
Line Inrush Current
115 VAC
5 volts and 80 amps
24 amps peak
Line Regulation
3. Output Section
The ac voltage present at the secondaries of T1 is rectified by four MBR6035
Schottky devices connected in a full wave center tapped configuration. Each
device is protected from excessive switching voltage spikes by an R-C snubber,
and output current sharing is aided by having separate secondary windings. Output
current limit protection is achieved by incorporating a current sense transformer
T4. The out-of-phase secondary halves of T1 are cross connected through the
core of T4, forming a I-turn primary. The 50 kHz output is filtered by inductor
L1, and capacitor C4. Resistor R4 is used to guarantee that the power supply
will have a minimum output load current of 1.0 ampere. This prevents the output
transistors Q3 and/or Q5 from cycle skipping, as the required on-time to maintain
regulation into an open circuit load is less than that of the devices' storage time.
Transformer T5 is used to reduce output switching spikes by providing common
mode noise rejection, and its use is optional.
The MC3423, U 1, is used to sense an overvoltage condition at the output,
and will trigger the crowbar S.C.R., Q8. The trip voltage is centered at 6.4 V
with a programmed delay of 40 ILs. In the event that a fault condition has caused
the crowbar to fire, a signal is sent to the control section via jumper 'A' or 'B.'
This signal is needed to shut down the output, which will prevent the crowbar
S.C.R. from destruction due to over dissipation. Automatic over voltage reset
is achieved by connecting jumper' A.' The control section will cycle the power
supply output every 2 seconds until the fault has cleared. If jumper 'B' is connected, S.C.R. Q12 will inhibit the output until the ac line is disconnected.
4. Low Voltage Supply Section
A low current internal power supply is used to keep the control circuitry
active and independent from external loading of the output section. Transformer
T2, Q9 and CR2 form a simple 14.3 V series pass regulator.
5. Control Section
The TL494 provides the pulse-width modulation control for the power supply.
The minimum output dead-time is set to approximately 4% by grounding Pin 4
through R5. The soft start is controlled by C5 and R5. Transistor Q 11 is used
to discharge C5 and to inhibit the operation of the power supply if a low ac line
voltage condition is sensed indirectly by QlO, or the output inhibit line is
grounded.
108
AC Input Section
Power SectlOn
.
T1
Output Section
~
120
11 I
11
47
10k
5W
'izW
lN4001
lOW
c 5V
10
80A
'hW
R4
~5R Cl.L 2400
~5A~~
J
~
I«
01
10 5A
3AG
46000
10V
C4
M eJ
8~
6-8
lOW
~2
Rl
100
~
5W
C2
1
0 1
>1
0
1
NI
"I
1
1
1
~""'ill
230
115
~--
....
0
CO
n
...".....,
1
1
I~t
~
.Lu..,.
T5=
.("VV
100 3
MCR
012
iG"
:B::~ 21111 11II
*"
1k
5VSEN RTN
oo
10
lk
Ij
! !
~
d,
2200
10V
t-
.1
1
__
T,
r--1rf"-t-t-........., 5 V SEN
MBR 6035
10k
5W
-
.+
j
j
'hW
c', V RTN
~OlJtpU(
Inhibit
10 'izW
.uu.
_, I'"
!,..,
I
t t
11 T3
';oR
22 k
09
~B2k
MPS
A 70
010
82 k
10
TIP 31
~ I;~r
IN
4933
1~6v
36
1W
C5
Jl'"
1
12
lOOA
TL 494
U,
7pB:tl
lN
,
4744.4
5
2153
6
I 0,01
10k~ i:),~
Wlln
1f
14 7k
~
1 MEG
Figure 13-3. 400 Watt SWITCHMODE Power Supply
18k
*'N
4001
CTI8>
0 0
0'"
C6
22
16V
All Capacitors In }IF
All ReSistors In
Ohms 1/4 Watt
(Unless otherWise noted)
T Output Section
Power Section
AC Input Section
~ j ~
~
),
1505A
3AG
68
lOW
Rl
115
5W
~
4800
~
"
4936
g
200 V
~t
.1
t
~
~
~
f47
'N
10 V
C'
1--1'1
4936
~'2V
MC~~23
:II[
'N
4936
MC3423
Ul
::'~R,
Q12
g
10k
hi"'i 'I'I'~
'm ~ I i ~;~?
roOD33
; +, I
T~v
lk
IILl
115V
230
I
11j
115
j
I
j
39hw
o
~T2
15kR
012 RTN
'oh,b"
~47k
4933
33
,
0
J
11
121
I
TL494
U2
IN
All Capacitors
4001
SRl
ell 8>
4744
:;'"
I
j
33K
lN
IN
2200
rQ",p",
j
MPS
A 70
Ql0
GTI 01 U'I WI
lN
4933
35V
j
I
22 k
low Voltage
o12SENRTN
J..[ 5.
.[
~
l§J
I ,
10
'hW
T~ ~ 1k
j
SEN
2200
10 V
5W
1115
'hW
46000
4936
'N
o12V,84A
10
lN4001
lOW
R'
0>
C2
11 !
j
68200V
~~*
(FAN
1230
~g
~
10k
160
14W
l;:
;;k
~
391f2W
]
C6
22
16V
1+
16V
Figure 13-4. 1000 Watt SWITCHMODE Power Supply
",F
IUnless otherwise noted)
-1-+
suLp_P-;-,y-:s:;-e-ct:CiQ~n~---4--il------=--:-I:--~--4------~-----------J'--_ _ _~J__~_-L_-.-!'''--L-~':'Ju~L-L--------------~----_e~--------~----------~----~~
Supply
RE
R
::r:: CE
R
VCC
DRV1
IE
M
C1+ C
C1- 3
Vref 4 IND2
C2+ 2
DLY1
4
Line Fault
T
---
--
12.6 V CT
-
DLY2
C2-
]
RL
CD
Figure 14·14. Sensing Line Fault and Over Voltage Conditions
for Linear and Switching Power Supplies
Input
Filter
From
Rectified
Line
R
Linear
Regulator
t---.----........ To Load
RE
R
RL
VCC
C1+
DRV1
C1- M
C
Vref 3 IND2
4
C2+ 2
4 DLY2
DLY1
C2IE
R
R
Line Fault
Gnd
ICE
- - --
-
--
II
Figure 14·15. An Alternate Method of Sensing Line Fault and Overvoltage Conditions
for Linear Power Supplies
132
and medium sized computer systems which must store part or all of the data
currently being processed before the power failure. The use of circuits such as
these will allow such systems to "die with dignity."
The circuits shown in Figures 14-14 and 14-15 both perform essentially the
same function. The circuit shown in Figure 14-14 may be used with almost any
type of regulator circuitry; however, the circuit shown in Figure 14-15 should
only be used in linear type supplies where the filter capacitor is isolated from the
line. Using the circuit in Figure 14-15 on switching supplies where the filter
capacitors are not isolated from the line would defeat the isolation in the switching
transformer.
The circuit shown in Figure 14-14 utilizes half of the MC3424 as an overvoltage protection circuit in a configuration like the programmable configuration
discussed earlier for the MC3423. The remaining half of the device is configured
for line loss and brownout detection. The C2 + and C2 - inputs are connected
as an undervoltage sensing circuit, and sense the center tap of a voltage divider
driven with a full wave rectified signal proportional to the line voltage. At each
peak of the line the output of the comparator discharges the delay capacitor (CD).
If a half cycle is missing from the line voltage, or if a brownout occurs reducing
the peak line voltage, the delay capacitor will not be discharged and will continue
to be charged as shown in Figure 14-16. If a sufficient number of half cycles are
missing, or if the brownout continues for a sufficient time, the circuit will detect
an ac line fault and output a line fault indication on the indicator outP~t. The
delay capacitor is used to provide some noise immunity and to prevent the loss
of a single half cycle from triggering the line fault signal. The minimum time the
fault condition must occur can be adjusted by changing the value of the delay
capacitor.
The circuit shown in Figure 14-15 senses the voltage on the power supply
filter capacitors to predict the imminent power supply failure. Since the voltage
on the capacitor is proportional to the remaining charge, the remaining time the
power supply will function can be calculated by the equation:
t
Where
=
C (Ve - Vmin)
C = filter capacitance
t = time to power supply failure
= maximum load current
Ve = filter capacitor voltage
Vmin = minimum regulator input voltage
Imax
By setting t equal to the maximum time for the system to store all required
data, and solving the equation for Vc, the minimum capacitor voltage can be
calculated that will allow the supply to remain functional, while the system
executes the power down sequence. The MC3424 is then configured as an undervoltage detector, as shown in Figure 14-15, and programmed to detect the minimum capacitor voltage Ve.
133
Rectified
Line
Vref
~5~-------------------
VCD
--I-_->--_"""
Line Fault
I--- Normal Line
Line
Conditions
L
---j-----
Brownout
- - - - - + - - Line Loss--1
«80% VNominal)
Figure 14-16. Waveforms Illustrating Brownout and Line Loss Detection for the Circuit of Figure 14-14.
REFERENCES
1. "Characterizing the SCR for Crowbar Applications," Al Pshaenich, Motorola
AN-789.
2. "Semiconductor Considerations for DC Power Supply SCR Crowbar Circuits," Henry Wurzburg, Third National Sold-State Power Conversion Conference, June 25, 1976.
3. "Is a Crowbar Enough?" Willis C. Pierce Jr., Hewlett-Packard, Electronic
Design 20, Sept. 27, 1974.
4. ''Transient Thermal Response-General Data and Its Use," Bill Roehr and
Brice Shiner, Motorola AN-569.
134
SECTION 15
HEATSINKING
A. THE THERMAL EQUATION
A necessary and primary requirement for the safe operation of any semiconductor device, whether it be an IC or a transistor, is that its junction temperature be
kept below the specified maximum value given on its data sheet. The operating
junction temperature is given by:
Tj = TA
where
+
PD (hA
(15.1)
Tj = junction temperature CC)
T A = ambient air temperature (0C)
= power dissipated by device (watts)
(JJA = thermal resistance from junction to ambient air (OC/W)
PD
The junction-to-ambient thermal resistance, OJA, in Equation (15.1) can be
expressed as a sum of thermal resistances as shown below:
(hA = OJC
where
+
+
Ocs
(15.2)
OSA
OJC = junction-to-case thermal resistance
()cs = case-to-heatsink thermal resistance
()SA
= heatsink-to-ambient thermal resistance
(Equation (15.2) applies only when an external heatsink is used. If no heatsink is used. OJA is equal to the device package ()JA given on the data sheet.)
()JC depends on the device and its package (case) type, while ()SA is a property
of the heatsink and ()cs depends on the type of package/heatsink interface
employed. Values for ()JC and ()SA are found on the device and heats ink data sheets,
while 8cs is given in Table 15-1.
TABLE 15-1
IIcs For Various Packages &
Mounting Arrangements
IIcs
METAL-TO-METAL *
CASE
DRY
USING AN INSULATOR*
With Heatsink
Compound
With Heatsink
Compound
Type
3 mil MICA
Anodized Aluminum
TO-3
O.2°CIW
O.1°CIW
O.36°CIW
O.28°CIW
TO-66
1SCIW
O.5°CIW
O.9°CIW
2 mil MICA
TO-220
1.2°CIW
1.0°CIW
1.6°CIW
2 mil MICA
*Typical values; heatsink surface should be free of oxidation, paint, and anodization
135
Examples showing the use of Equations 15. 1 and 15.2 in thermal calculations
are as follows:
Example 1: Find required heatsink OSA for an MC7805CT; given:
Tjrnax (desired) = + 125°C
T Arnax = + 70°C
PD = 2 watts
Mounted directly to heats ink with silicon thermal grease at interface
1. From MC7805CT data sheet, (he = 5°C/W
2. From Table 15-1, 8cs = 2.6°C/W
3. Using Equation 15.1 and 15.2, solve for OsA:
OSA =
OSA
(TJ
-
TA)
PD
-
Ocs - OJC
= (125 ;- 70) - 5.0 - 2.6
~
19. 9°C/W required
Example 2: Find the maximum allowable TA for an unheatsinked
MC78L15CT, given:
Tjmax (desired) = + 125°C
PD
= .25 watt
1. From MC78L15CT data sheet, OJA = 200°C/W
2. Using Equation 15.1 find TA:
T A = Tj - PD OJA
125 - .25 (200)
+75°C
B. SELECTING A HEATSINK
Usually, the maximum ambient temperature, power being dissipated, the
Tjrnax, and O~e for the device being used are known. The required OsA for the
heats ink is then determined using Equations 15. 1 and 15.2, as in Example 1.
The designer may elect to use a commercially available heatsink, or if packaging
or economy demands it, design his own.
1. Commercial Heatsinks
As an aid in selecting a heatsink, a representative listing is shown in Table
15-2. This listing is by no means complete and is only included to give the
designer an idea of what is available.
136
TABLE 15-2
Commercial Heatsink Selection Guide
No attempt has been made to provide a complete list of all heatsink manufacturers. This list is only
representative.
TO-3 & TO-66
!JsATC/W)
Manufacturer/Series or Part Number
0.3-1.0
Thermalloy -
6441, 6443, 6450, 6470, 6560, 6590, 6660, 6690
1.0-3.0
Wakefield - 641
Thermalloy - 6123, 6135, 6169, 6306, 6401, 6403, 6421, 6423, 6427,
6442, 6463, 6500
3.0-5.0
Wakefield - 621, 623
Thermalloy - 6606, 6129, 6141, 6303
IERC- HP
Staver - V3-3-2
5.0-7.0
Wakefield - 690
Thermalloy - 6002, 6003, 6004, 6005, 6052, 6053, 6054, 6176,6301
IERC- LB
Staver - V3-5-2
7.0-10.0
Wakefield - 672
Thermalloy - 6001, 6016, 6051, 6105, 6601
IERC - LA, uP
Staver - V1-3, V1-5, V3-3, V3-5, V3-7
10.0-25.0
Thermalloy -
6013, 6014, 6015, 6103, 6104, 6105, 6117
'All values are typical as given by mfgr. or as determined from characteristic curves supplied by
manufacturer.
TO-S
!JSA*("C/W)
Manufacturer/Series or Part Number
12.0-20.0
Wakefield - 260
Thermalloy - 1101, 1103
Staver - V3A-5
20.0-30.0
Wakefield - 209
Thermalloy - 1116, 1121, 1123, 1130, 1131, 1132, 2227, 3005
IERC- LP
Staver - F5-5
30.0-50.0
Wakefield - 207
Thermalloy - 2212,2215,225,2228,2259,2263,2264
Staver - F5-5, F6-5
Wakefield - 204, 205, 208
Thermalloy - 1115, 1129, 2205, 2207, 2209, 2210, 2211, 2226, 2230,
2257, 2260, 2262
Staver - F1-5, F5-5
OSA*(OCIW)
CASE TO-220
5.0-10.0
IERG H P3 Series
Staver - V3-7-225, V3-7-96
10.0-15.0
Thermalloy - 6030, 6032, 6034
Staver - V4-3-192, V-5-1
15.0-20.0
Thermalloy - 6106
Staver - V4-3-128, V6-2
20.0-30.0
Wakefield - 295
Thermalloy - 6025, 6107
*AII values are typical as given by mfgr. or as determined from characteristic curves supplied
by manufacturer.
137
TO-92
OSA*(OC/W)
46
50
57
65
72
80-90
85
Manufacturer/Series or Part Number
Staver F5-7A, F5-8
IERC RUR
Staver F5-7D
IERC RU
Staver F1-8, F2-7
Wakefield 292
Thermalloy 2224
DUAL-INLINE-PIN ICS
20
30
32
34
45
60
Thermalloy - 6007
Thermalloy - 6010
Thermalloy - 6011
Thermalloy - 6012
IERC - LlC
Wakefield - 650,651
* All values are typical as given by mfgr. or as determined from characteristic curves supplied by
manufacturer.
Staver Co., Inc.: 41-51 N. Saxon Ave., Bay Shore, NY 11706
IERC: 135 W. Magnolia Blvd., Burbank, CA 91502
Thermalloy: P.O. Box 34829, 2021 W. Valley View Ln. Dallas, TX
Wakefield Engin Ind: Wakefield, MA 01880
2. Custom Heat Sink Design
Custom heats inks are usually either forced air cooled or convection cooled.
The design of forced air cooled heatsinks is usually done empirically, since it is
difficult to obtain accurate air flow measurements. On the other hand, convection
cooled heatsinks can be designed with fairly predictable characteristics. It must be
emphasized, however, that any custom heats ink design should be thoroughly tested
in the actual equipment configuration to be certain of its performance. In the
following sections, a design procedure for convection cooled heatsinks is given.
Obviously, the basic goal of any heatsink design is to produce a heats ink with
an adequately low thermal resistance, ()SA. Therefore, a means of determining ()SA is
necessary in the design. Unfortunately, a precise calculation method for ()SA is
beyond the scope of this book. * However, a first order approximation can be
calculated for a convection cooled heats ink if the following conditions are met:
1. The heats ink is a flat rectangular or circular plate whose thickness is much
smaller than its length or width.
2. The heats ink will not be located near other heat radiating surfaces.
3. The aspect ratio of a rectangular heats ink (length:width) is not greater than 2: 1.
4. Unrestricted convective air flow.
For the above conditions, the heatsink thermal resistance can be approximated by:
()SA
where
= AT)
(Fch~ + EHr) (OC/W)
A
area of the heatsink surface
T)
heatsink effectiveness
(15-3)
*If greater precision is desired, or more information on heat flow and heatsinking is sought, consult the references
list at the end of this section.
138
Fe = convective correction factor
he
E
convection heat transfer coefficient
=
emissivity
Hr = normalized radiation heat transfer coefficient
The convective heat transfer coefficient, he, can be found from Figure 15-1.
Note that it is a function of the heatsink fin temperature rise, Ts - TA, and the
heatsink significant dimension, L. The fin temperature rise, Ts
TA, is given
by:
(15.4)
Ts - T A = ()SA PD
where
Ts
heats ink temperature
TA
ambient temperature
heatsink-to-ambient thermal resistance
()SA
power dissipated
PD
10
9.0
8.0
:~
...c:
'"
M
't't-
0'
7.0
8 ...
6.0
0
5.0
U
c:
°
x
.., a I
~ N
> c: 4.0
°c: .-. .
U ~
;:,
3.0
.c:
....-
L = 1"
~
~ k-'
I--"
V k....~
~
r~I
~ "';'y ~
~
----- ~
V--
---
2.0
10
20
30
Ts·T A
•
---
50
.-1-"
.-1-"
.-f-"
.-1-"
70
-----------
~
.......-
100
200
Fin Temperature Rise (oC)
Figure 15-1. Convection Coefficient, hc
The significant heatsink dimension, L, is dependent on the heatsink shape
and mounting place and is given in Table 15-3.
The convective correction factor, Fc, is likewise dependent on shape and
mounting plane of the heatsink and is also given in Table 15-3.
TABLE 15-3
Significant Dimension L and Correction Factor Fe for
Convection Thermal Resistance
Significant Dimension L
Surface
Position
vertical
Rectangular Plane
horizontal
Circular Plane
vertical
L
height -
(max 2 tt)
length x width
length + width
7T
/1 x diameter
139
Correction. Factor Fe
Position
Fe
Vertical Plane
1.0
Horizontal Plane
both surfaces
exposed
1.35
top only exposed
0.9
The normalized radiation heat transfer coefficient, Hr, is dependent on the
ambient temperature, TA, and the heats ink temperature rise, Ts - TA, given by
Equation (15.4). Hr can be determined from Figure 15-2.
2.0
...c:
"
L
CI>
'0
1.5
ij:
./ " " /
~ ~
o° 0...
c:
~
...... ...... / / / /
x
0
1 .0
~ °1 0.9
~ ~ 0.8
"0
-
.~ ~ 0.7
iii
~ 0.6
~
0.5
E~
r....
= 1000C
,T
-
0.4
10
A
-
l--'
...--
vi"""
75°C
~~
50°C
I---- ~
~
:.,..;;-I--
25°C
Vi"""
30
20
~
50
,......,
..... ~
............
........
........
""L
./ /
/'
:."./
~
70
100
200
Ts -T A, Temperature Rise of Plate (oC)
Figure 15·2. Normalized Radiation Coefficient, Hr
The emissivity,
E,
can be found in Table 15-4 for various heats ink surfaces.
TABLE 15·4.
Typical Emissivities of Common Surfaces
Surface
Aluminum, Anodized
Alodine on Aluminum
Aluminum, Polished
Copper, Polished
Copper, Oxidized
Rolled Sheet Steel
Air Drying Enamel (any color)
Oil Paints (any color)
Varnish
Emissivity,
€
0.7 - 0.9
0.15
0.05
0.07
0.70
0.66
0.85 - 0.91
0.92 -0.96
0.89 -0.93
Finally, the heatsink efficient, T'J, can be found from the nomograph of Figure
15-3. Use of the nomograph is as follows:
a. Find hT = Fchc + EHr from Figures 15-1, 15-2 and Tables 15-3 and 15-4,
and locate this point on the nomograph.
b. Draw a line from hT through chosen heatsink fin thickness, x, to find a.
c. Determine D for the heatsink shape as given in Figure 15-4 and draw a line
from this point through a, which was found in (b), to determine T'J.
d. If power dissipating element is not located at heats ink's center of symmetry,
multiply T'J by 0.7 (for vertically mounted plates only).
Note that in order to calculate (!sA from Equation (15.3), it is necessary to
know the heatsink size. Therefore, in order to arrive at a suitable heatsink design,
a trial size is selected, its (!sA evaluated, and the original size reduced or enlarged
as necessary. This process is iterated until the smallest heats ink is obtained that
has the required (!sA. The following design example is given to illustrate this
procedure:
140
o
4.0
3.0
'"
0.05
r
Fin Thickness
2.0
0.1
,., ~
Aluminuf
0.2
1.0
0.8
0.7
0.6
0.5
~
1.0
1.0
0.1
0.4
2.0
~
~
0.3
0.4
0.5
0.3
0.2
3.0
4.0
5.0
10
10
11
Fin Effectiveness
10
1.0
1.0
0.1
94
0.01
0.01
0.1
90
88
85
0.001
0.001
84
r-0.0001
Inches
Inches
hT = FChC+EHr
0.01
82
80
75
70
10.0
65
0.001
60
55
Watts/IN2/ C
50
45
40
35
%
Figure 15-3. Fin Effectiveness Nomogram for Symmetrical Flat, Uniformly Thick Fins
Tf--L- - - - r /
a
1'---~-b--j--!'l
D'="Jii.
D"'!'!
2
if a,b;l>S &
if d;l>s
b~2a
Figure 15-4. Determination of D for Use in 11 Nomograph of Figure 15-3
Heatsink Design Example
Design.a flat rectangular heatsink for use with a horizontally mounted power
device on a PC card, given the following:
1. Heatsink ()SA = 25°C/W
2. Power to be dissipated, PD = 2W
3. Maximum ambient temperature, TA = 50°C
4. Heatsink to be constructed from Vs" (0.125") thick anodized aluminum.
a. First, a trial heatsink is chosen: 2" x 3" (experience will simplify this selection
and reduce the number of necessary iterations.)
b. The factors in Equation (15.3) are evaluated by using the Figures and Tables
given.
A = 2" x 3" = 6 sq. in.
L = 6/5" = 1.2 in. (from Table 15-3)
Ts - TA = 50°C (from Equation 15.4)
he = 5.8 X 10- 3 W/in 2 - °C from Figure 15-1)
Fe = 0.9 (from Table 15-3)
Hr = 6.1 X 10- 3 W/in 2 - °C (from Figure 15-2)
e = 0.9 (from Table 15-4)
hT = Fehe + Hre = 10.7 X 10- 3 w/in 2 - °C
ex = 0.13 (from Figure 15-3)
D = 1. 77 (from Figure 15-4)
'Y) > 0.94 = 1 (from Figure 15-3)
c. Using Equation 15.3, find ()sA
()SA
=
AT}
(Fc~ + EHr)
= 16.66°C/W < 25°C/W
d. Since 2" x 3" is too large, try 2" x 2". Following the same procedure,
found to be 25°C/W, which exactly meets the design requirements.
142
()SA
is
REFERENCES
1. Bill Roehr, "Motorola Silicon Rectifier Handbook," Chapter 10, Motorola
Inc., 1973.
2. Werner Luft, "Taking the Heat Off Semiconductor Devices," Electronics,
June 12, 1959.
3. Frank Kreith, Principles of Heat Transfer, International Textbook Co., 1958.
143
144
SECTION 16
REGULATOR RELIABILITY
A. QUALITY CONCEPTS
The quality of a regulator, from a production line, is a measure that expresses
the conformance of the device to a set of specifications. Such a measure is the
percent rejects out of a collection of devices (lot, population). One hundred percent
inspection has to be used to determine the quality of the lot. One characteristic of
this approach is that it is expensive, and therefore, is used only where necessary. In
addition, it may not be as accurate as it first appears because of operator errors due
to fatigue and of course, it cannot be used where the inspection (test) is destructive.
An alternative to this is scientific acceptance sampling. Acceptance sampling is a
method by which a portion of the total population is examined. On the basis of the
sample quality, (number of rejects out of a total sample that fail to conform to
specifications) and by using the mathematics of probability and statistics, an
estimate of the lot quality is made and the risk of an improper decision is specified.
For example, a lot may be rejected because the sample quality was less than that
prescribed by the mathematics of sampling and our original goal (maximum percent
rejects allowed in a lot). Yet, if the lot was one hundred percent inspected, we may
find that the actual percent rejects in the lot was less than the maximum percent
rejects established as a goal (Type I improper decision). In a similar way, the
reverse may happen: a lot may be accepted on the basis of the sample quality
(sample rejects are fewer than those prescribed by the mathematics of sampling and
our goal) and yet, if a 100% inspection was performed, the actual percent rejects in
the lot could be more than our established goal (Type II improper decision). A
sampling plan is specified by the sample size and the maximum allowable defectives (known as the acceptance number (ACCN)).
The risks involved in sampling are described by the operating characteristic
(0. C.) curve ofthe sampling plan. As illustrated by Figure 16-1, this curve shows
the probability of acceptance, on the vertical axis, vs the lot quality (percent
rejects), on the horizontal axis. Each particular sampling plan will have its own
O.C. curve.
Two points on the curve are of interest. TheAQL, (acceptable quality level),
signifies the quality level that will be accepted most of the time (usually this is set at
95%). In other words, the AQL specifies the risk of making the Type I improper
decision, that is why it is often referred to as Producer's Risk. The other point on the
curve is the LTPD (lot tolerance percent defective) which signifies the level of
rejects in a lot that is unsatisfactory and should be rejected by the plan most of the
time (usually this is set at 10%). This is also known as Consumer's Risk.
145
100%
~--
90%
----
~6L
80%
"c
I
I
u
60%
I
I
50%
I
.~
I
.!l
I
I
I
'"
.!l
e
\
I
"uu
«
'0
\
I
70%
!!0.
'"'\
I
I
I
I
40%
Q.
\
\
I
30%
I
I
20%
10%
---
- -
I
I
-..,. -
-
I
-
\
\
------~
I
0.1
0.2
0.3
0.4
•
•
•
•
•
•
•
•
•
•
•
•
•
• %
Lot Quality (Percent Defective)
Figure 16-1. Typical Operating Characteristic (O.C.) Curve
Regulators can be produced to a variety of quality levels by combining
different 100% and sample inspections and varying the criteria of acceptance and
rejection. Thus, a customer can negotiate his own custom quality level if he
wishes; however, this can become quite expensive in terms of time and money.
That is why Motorola, in addition to the standard product level, produces regulators
to four different levels of quality that are similar to those found in the MIL-M38510 JAN Program processed in accordance with MIL-STD-883. The Motorola
program is called MIL-M-3851O JAN Processed Product; a description of the
program is beyond the scope of this section, however, Table 16-1 gives the
outgoing quality assurance sampling plan for standard quality level regulators.
It is important to discern the effects of the different quality levels. This can be
done by noting the typical field removal rates (verified rejects plus removed
devices verified good) for different classes of 38510 integrated circuits listed
below.
Field Removal Rate/ 1000 hours
Commercial (no burn-in)
Class C
Class B
Class A
0.1%
0.04%
0.004%
0.002%
146
TABLE 16-1
Outgoing Quality Assurance Sampling Plan
for
Regulators Standard Product
Subgroups
(Per Mil-Std-883, Method 5005)
A-I:
A-2:
A-3:
A-4:
A-5:
A-6:
A-7:
A-8:
A-9:
A-21:
Static Tests, 25°C
Static Tests, Max. Temp.
Static Tests, Min. Temp.
Dynamic Tests, 25°C
Dynamic Tests, Max. Temp.
Dynamic Tests, Min. Temp.
Funct. Test, 25°C
Funct. Test, MiniMax Temps.
Switching Tests, 25°C
Key Parameters, 25°C
LTPD
ACCN
2.3
3.8
3.8
2.3
3.8
3.8
2.3
2.3
2.3
2.3
0
1
1
0
1
1
0
0
0
0
AQL
0.11
0.11
0.11
Although the above removal rates are not specifically for regulators, because
these products are relatively new with respect to other integrated circuits, nevertheless, it is expected that regulators will have similar removal rates. Burn-in can be
used to improve the failure rate of regulators. As a rule of thumb, a 10 to 1
improvement may be realized. This is because regulators are state-of-the-art
devices, handling high voltages and currents.
B. RELIABILITY CONCEPTS
Reliability is the probability that a regulator will perform its specified function
in a given environment for a specified period of time. The most frequently used
reliability measure for regulators is the failure rate, expressed in percent per
thousand hours. The number of rejects observed, taken over the number of device
hours accumulated at the end of the observation period and expressed as a percent,
is called thepoint estimate failure rate. This, however, is a number obtained from
observations from a portion of all the regulators; if we are to use this number to
estimate the failure rate of all regulators (total population), we need to say something about the risk we are taking by using this estimate. This statement is provided
by the confidence level expressed together with the failure rate. For example, a
0.1 % per 1000 hours failure rate at 90% confidence level means that 90% of the
regulators will have a failure rate below 0.1 %/1000 hrs - mathematically, the
failure rate at a given confidence level is obtained from the point estimate and the
CHI square (X2) distribution. (The X2 is a statistical distribution used to relate the
observed and expected frequencies of an event). In practice, a reliability calculator
rule is used that gives the failure rate at the confidence level desired for the number
of rejects and device hours under question.
It is also important to note that, as the number of device hours increases,
our confidence in the estimate increases. In integrated circuits, it is preferred to
make estimates on the basis of 1,000,000,000 device hours or more. If such large
numbers of device hours are not available for a particular device, then the point
estimate is obtained from devices that are similar in process, voltage, construction,
design, etc., and for which we expect to see the same failure modes in the field.
147
Finally, the environment is specified in terms of the junction temperature of
the regulator by using one of the following two expressions:
(A) TJ
= TA +
OJAPO
(B) TJ
=
OJC
or
where
TJ
=
Tc
+
Po
Junction Temperature
TA
Ambient Temperature
Tc
Case Temperature
OJA
Junction to Ambient Thermal Resistance
OJC
Junction to Case Thermal Resistance
Po
=
Power Dissipation
100
I I
Typical Failure Rate
vs
Junction Temperature
for R egu lators
Non-burned-in Product
10
,\
cn_
a: .,
:r
oo
o
~
-'
.,
()
\
.,
~
c:
......
-*' ....~
., c:
...
., u0
~ ~
~
g
i\
0.1
\
~ @J
u.
0.01
\
0.001
500
400
300
200
150
100
Junction Temperature
Figure 16-2
148
0
C
50
25
One other point worth remembering is that the failure rate for integrated circuits
increases as the junction temperature increases while the causes of failure generally
remain the same. Thus, we can test devices near their maximum junction temperatures, analyze the failures to assure that they are the types that are accelerated
by temperature and then by applying known acceleration factors, estimate the
failure rates for lower junction temperatures. Figure 16-2 shows a curve that gives
estimates of typical failure rates vs temperature for regulators. To assure that the
reliability level does not change over a period of time, Motorola performs a
number of periodic audits such as EPIIC. These audit programs, besides monitoring the current reliability level, provide information on what will be required
to achieve higher levels of reliability.
Frequently a question is raised about the reliability differences betweenplastic
vs hermetic regulators. In general, for all Linear integrated Circuits, including
regulators, the field removal rates for plastic and hermetic I/C's are the same for
environments where there is no high humidity. In cases where the environment
contains high humidity, higher failure rates are to be expected from plastic encapsulated devices. On the other hand, some users have reported favorabte results in
moderate humidity environments when boards with plastic I/C's (including regulators) are coated with protective materials, provided that the coating is done
properly (adhering properly) and no new contaminants are introduced.
149
150
SECTION 17
IC REGULATOR SELECTION GUIDES
The selection guides in this section are included as an aid to choosing an
appropriate IC regulator. These guides are organized according to regulator type
and list all the IC voltage regulators presently offered by Motorola.
A. ADJUSTABLE OUTPUT REGULATORS
When an adjustable output voltage is required, use of the regulators shown
in Table 17-1 is recommended. Output voltage is set by adjusting the value of
an external resistor or resistors. More complete data on individual devices can
be found in the data sheets of Section 18. An explanation of the column headings
shown in Table 17-1 follows:
Maximum Output Current (10 max)
Maximum output current in which key device parameters are specified.
Device
Motorola part number for the IC regulator.
Suffix
Designator for case type; and, in some products, includes temperature range.
Output Voltage (Vout)
The range of output voltages that can be obtained with the regulator basic
circuit configuration. (Methods for extending output voltage range are shown in
Section 3.)
Input Voltage (V in )
Range of allowable DC input voltages. These are instantaneous values.
Exceeding maximum input voltage could result in regulator damage, while dropping below minimum value will cause loss of regulation.
Input-Output Differential (V in- Vout)
This is the minimum voltage across the regulator for proper operation.
Maximum Power Dissipation (PD max)
Maximum power the device can dissipate in free air at T A = 25°C without
a heatsink; and with case temperature held constant at Tc = 25°C.
151
Line Regulation (Regline)
The percent change of output voltage for a change in input supply voltage.
Given by:
Regline (%) =
~Vout
Vx
out
where
~ V out
=
4 Vin
= change in Vin
change in
1
~y.
m
x
100
V out
This performance figure applies for the entire output and input voltage range
for the regulator. For actual test conditions, consult data sheets in Section IS.
Load Regulation (Regload)
The percent change of output voltage for a change in output current. For
actual test conditions, consult data sheets in Section 18.
Typical Temperature Coefficient of Output Voltage (Tc of Vout)
Percent change in output voltage per degree Celsius rise in junction temperature.
Maximum Operating Junction Temperature (TJ max)
Maximum junction temperature allowed before damage occurs. For complete
thermal information consult data sheets in Section 18. See Section 15 for heatsinking techniques.
Packages
Case
Case
Case
Case
Case
Case
Case
Case
Case
Case
1: "TO-3" metal can
29: "TO-92" plastic package
79: "TO-39" metal can
80-02: "TO-66" metal can
221A: "TO-220" plastic package
603: to-pin "TO-5" metal can
614: 9-pin "TO-66" metal can
632: 14-pin ceramic dual-in-line package
646: 14-pin plastic dual-in-line package
751A: 14-pin plastic dual-in-line SOIC package
For detailed outline drawings of these case styles, consult Section 19.
152
TABLE 17·1
ADJUSTABLE OUTPUT REGULATORS
POSITIVE OUTPUT REGULATORS
S
U
mA
Mu
Device
Type
I
X
Min
Max
Min
Max
VinVout
Differential
Volts
Min
100
LM317L
H,Z
1,2
37
5,0
40
3,0
Vout
Volts
F
F
10
Vin
Volts
LM217L
Regulation
%Vout@
TA = 25"<:
Typ
Po
Watts
Max
=
TA
25"<:
=
TC
25"<:
Internally
Limited
MC1723
~
~
~
2,0
37
9,5
40
3,0
r------
~
CD
MC1469
G
2,5
MC1569
500
%I"C
Max
Case
0.04
0,5
0,006
125
29,79
0,02
0,3
0,004
150
LM317M
T
LM317M
R
1,2
32
9,0
35
3,0
37
8.5
40
2,7
37
5,0
40
3,0
1,25
-
0,1
1,0
2,1
~
0,003
0,2
0,002
1,5
-
0,1
0,003
0,2
0,002
1.25
-
0,68
1,8
0,3
0,1
Internally
175
632
150
751A
~
0,015
0,002
150
603
0,02
0,1
0.0056
125
221A
0,004
150
80
0,0036
R
2,5
LM317
T
LM317
H,K
1,2
32
9,0
35
3,0
37
8.5
40
2,7
37
5,0
40
3,0
3,0
14,0
Internally
~
0.Q15
0,05
0,002
150
614
0,07
1,5
0,006
125
221A
Limited
79,1
LM217
0,004
0,05
1.0
0,003
150
0,02
0,1
0,008
125
LM250
0,0057
150
LM150*
0,0051
LM117*
3000 :'
646
603C
limited
MC1569
1500
150
0,003
LM117M*
MC1469
0,003
0,13
LM217M
600
=
"<:
Load
0.003
CL
250
TJ
Line
LM117L*
150
TC Vout
Typ
LM350
T
LM350
K
1,2
33
5,0
36
3,0
Internally
Limited
221A
1
#TJ = -40 to +125·C
*TJ= -55to+150·C
tOutput Voltage Tolerance for Worst Case
NEGATIVE OUTPUT REGULATORS
S
M..
Type
U
F
F
I
X
250
MC1463
G
to
mA
Devlca
MC1563
600
MC1463
R
MC1563
1500
LM337
T
LM337
H,K
Regulation
%Vout@
TA
25"<:
Typ
Po
Max
VinVout
Differential
Volts
Min
TA
25"<:
TC
25"<:
Lina
Load
%I"C
Max
Case
35
3,0
0,68
1,8
0,03
0,05
0,002
150
603
8,5
40
2,7
0,015
0,13
-34
9,0
35
3,0
~
0,05
0,002
175
614
-37
8,5
40
2,7
-37
5,0
40
3,0
0,3
0,0048
125
Vin
Volts
Vout
Volts
Min
Mu
Min
-3,8
-32
9,0
-3,6
-33
-3,8
-3,6
-1.2
Watts
Max
=
2,4
=
=
9,0
TC Vout
Typ
Internally
Limited
0,02
221A
79,1
LM237
0,0034
0,0031
153
=
"<:
0,015
LM137*
*TJ = -55to +150·C
TJ
150
B. FIXED OUTPUT REGULATORS
If low cost and easy implementation are prime regulator design considerations, the fixed output, three terminal regulators shown in Table 17-2 are recommended. These are available with output current capabilities from 100 rnA to
3.0 A. All have internal overcurrent, safe-operating area, and thermal protection
circuitry. Complete device specifications are given in the data sheets of Section
18. An explanation of the column headings shown in Table 17-2 follows:
Output Voltage (Vout)
Nominal output voltage for positive and negative regulators. The adjacent
column indicates worst case tolerance (Volts). (Methods for adjusting output
voltage are shown in Section 3.)
Maximum Output Current (10 max)
Maximum output current available from regulator under normal operating
conditions. (Methods for obtaining greater output currents are shown in Section 3.)
Device
Two columns are provided listing Motorola part numbers for positive and
negative voltage outputs.
Input Voltage minimax (Vin )
Range of allowable instantaneous de input voltage. Exceeding maximum Vin
could .result in regulator damage, while dropping below minimum value will
cause loss of regulation.
Line Regulation (Reg1ine)
Change in output voltage for a given change in input voltage. Test specifications are given in the '!ata sheets of Section 18.
Load Regulation (Regload)
Change in output voltage for a given change in output current. Test specifications are given in the data sheets of Section 18.
Typical Temperature Coefficient of Output Voltage (~V/~T)
Typical change in output voltage per degree celsius change in junction temperature.
154
Packages
Case 1: "TO-3" metal can
Case 29: "TO-92" plastic package
Case 79: "TO-39" metal can
Case 221A: "TO-220" plastic package
For detailed outline drawings of these case styles, consult Section 19.
Package
Styles
1~i3@"'2~
@
o
2
0
01
C
I ~ ~ ~0-';~-0
~
·0'''''23
' ,
CASE
1
(TO-3)
29
(TO-92)
79
(TO-39)
80
(TO-66)
221A
(TO-220)
MATERIAL
Metal
Plastic
Metal
Metal
Plastic
Metal
K
P, Z
G,H
R
T
G
SUFAX
C::::::I c:::J
,
9
614
(TO-66)
I
I
Metal
Metal
G
R
14
14
16
18
18
1
"
1
1
1
1
c:J G?::J 1;::::::::1 c::J
0
1
620
632
(TO-116)
646
648
707
726
751A
Ceramic
Ceramic
Plastic
Plastic
Plastic
Ceramic
Plastic
J, L
L
P
N,P
CASE
SUFAX
.. -
603
603C
(TO-5 Type)
16
MATERIAL
2
J
N
0
TABLE 17-2
FIXED OUTPUT VOLTAGE REGULATORS
FIXEDNOLTAGE, 3-TERMINAL REGULATORS FOR POSITIVE OR NEGATIVE POLARITY POWER SUPPLIES,
Vout
Volts
Tol.t
Volts
10
mA
Max
2
±O.1
1500
±0.15
100
3
5
Device Type
±O.5
±0.4
1.0
1,221A
60
72
-
29,79
60
-
29,79
100
1.0
79,221A
1.1
1,79
MC7902C
5.5135
-
MC79L03AC
4.7130
MC79L05C
MC79L05AC
MC78M05C
-
LM109
-
LM209
-
200
150
7135
±0.25
LM309
-
±0.35
MC7805*
-
8,0135
±0.25
MC7805B#
-
8135
"'0.2
MC7805A*
MC7805C
Regl~ad
80
6.7130
MC78L05C
MC78L05AC
500
3000
120
-
1500
±0.25
Case
40
Regline
mV
Vin
MC79L03C
100
AVOIIH
mVrC
Typ
MiniMax
±0.3
±0.25
mV
Device Type
Negative Output
Positive Output
100
50
1.0
100
0.6
1
1.0
1,221A
7/35
MC7905C
-
7.5135
MC7805AC
MC7905AC
LM140-5*
-
7135
LM340-5
7.3135
10
50
0.6
1,221A
50
50
1
10
25
MC78T05*
-
MC78T05C
-
MC78T05A*
-
1
MC78T05AC
-
1,221A
LM123*
LM223
-
LM323
-
0.1
+0.25
1
1,221A
±0.2
±0.4
1
100
7.5/20
5.0
25
-
1
I
(continued)
155
Fixed Output Voltage Regulators (continued)
Vout
Volts
Tol.t
Volts
10
mA
Max
Device Type
Positive Output
Device Type
Negative Output
Vin
MiniMax
Regline
mV
Regload
mV
mvrc
Typ
Case
5.2
±0.26
1500
-
MC7905.2C
7.2/35
105
105
1.0
1,221A
±O.3
500
MC7SM06C
-
S/35
100
120
1.0
79,221A
±0.35
1500
MC7S06*
9/35
60
100
0.7
9/35
120
120
6
A.VO/I1T
±O.3
MC7S06B#
-
MC7S06C
MC7906C
±0.24
MC7S06A*
-
B.6/35
LM140-6*
-
S/35
LM340-6
S.3/35
MC7B06AC
±0.3
3000
S
±O.S
100
MC7BT06*
-
MC7ST06C
-
MC7SLOSC
MC7S0SB#
-
MC7SLOBAC
±0.4
500
MC79MOBC
1500
MC7S0S*
±0.3
±O.4
3000
MC7BOSC
MC790SC
MC7S0SA*
-
MC7S0SAC
-
LM140-S*
-
LM340-S
-
MC7STOS*
-
MC7STOSC
12
±1.2
100
500
MC7SM12C
MC7S12*
MC7B12B#
-
±0.6
-
MC7S12AC
-
LM140-12*
MC7ST12A*
-
MC7BT12AC
-
LM340-12
3000
MC7BT12*
MC7ST12C
±0.5
±1.5
100
±O.6
1.0
100
1
11.5/35
160
160
1,221A
13
50
1
100
1,221A
1
10.5/35
SO
SO
10.4/35
13
25
0.16
-
13.7/35
250
100
14/35
100
240
1.0
15.5/35
120
120
1.5
240
240
1
29,79
79,221A
1
l,221A
14.5/35
14.S/35
IS
50
1
100
1,221A
14.5/35
120
120
1.5
14.5/35
IS
25
0.24
1
1
l,221A
1
l,221A
300
150
-
29,79
17/35
100
300
1.0
79,221A
lS.5/35
150
150
1.S
300
300
16.7/35
MC7B15B#
-
MC7S15C
MC7915C
17.5/35
MC7S15A*
-
17.9/35
LM140-15*
-
17.5/35
LM340-15
17.5/40
-
79,221A
160
MC7S15*
-
29,79
SO
MC7SM15C
MC7ST15*
1
100
500
MC7ST15C
0.12
10/35
1500
3000
25
11.5/35
MC7S115C
±0.75
11
-
MC7SL15A
MC7S15AC
1
BO
MC7SL15C
±0.6
60
200
175
MC7SL15AC
±0.75
60
1,221A
1500
MC7912C
1
1,221A
10.5/35
MC79L12C
MC7S12C
50
100
9.7/30
10.6/35
MC79L12AC
MC7S12A*
11
1,221A
MC7B112C
±O.5
15
B/35
MC7SL12AC
±0.6
1
1,221A
1
1,221A
50
1
100
l,221A
150
150
1
22
25
22
0.3
1
l,221A
MC7ST15A*
-
1
MC7ST15AC
-
1,221A
(continued)
156
Fixed Output Voltage Regulators (continued)
Vout
Volts
Tol.t
Volts
10
mA
Max
18
±1.8
100
Vin
MinIMax
Regline
Positive Output
Device Type
Negative Output
mV
Regload
mV
MC78L18C
MC79L18C
19.7/35
325
170
Device Type
MC78L18AC ,
"0.9
..WOI:'T
mvrc
Typ
-
MC79L18AC
500
MC78M18C
-
20/35
100
360
1.0
1500
MC7818*
-
22/35
180
180
2.3
MC7818B#
-
360
360
MC7818C
MC7918C
"0.9
3000
31
MC7818AC
LM140-18*
-
LM340-18
-
MC78T18*
-
MC78T18C
-
20.6/40
"'1.0
500
MC78M20C
24
,,2.4
100
MC78L24C
MC79L24C
MC78L24AC
MC79L24AC
50
1
100
1,221A
180
180
1
31
25
0.36
22/40
10
400
1.1
79,221A
350
200
-
29,79
300
500
MC78M24C
-
26/40
100
480
1.2
MC7824*
-
28/40
240
240
3.0
MC7824B#
-
480
480
MC7824C
±1.2
3000
-
MC7824AC
-
LM140-24*
-
LM340-24
-
79,221A
1
1,221A
27/40
MC7924C
MC7824A*
1
25.7/40
1500
"1.0
1
1,221A
1,221A
20
±1.2
79,221A
21/35
-
MC7818A*
"0.7
Case
29,79
27.3/40
MC78T24*
26.7/40
MC78T24C
50
1
100
1,221A
240
240
1
36
25
36
0.48
1
1,221A
#TJ ~ -40to +125"C
*TJ ~ -55 to + 150"C
tOutput Voltage Tolerance for Worst Case
C. SPECIALTY REGULATORS AND SWITCHING REGULATOR
CONTROL CIRCUITS
In addition to the regulators of Tables 17-1 and 17-2, Motorola offers two
specialty regulators: the MC1568/MC1468 ± 15 V Tracking regulator and the
MC1466 Precision Floating regulator. General specifications for these regulators
are shown in Table 17-3. More complete data on these devices can be found in
the data sheets of Section 18. An explanation of the column headings shown in
Table 17-3 follows:
Device
Motorola part number for the IC regulator. (No symbol indicates O°C to
+ 70°C operating ambient temperature range. * indicates - 55°C to + 125°C
operating ambient temperature range.)
Output Voltage (V0)
For the tracking regulators, the value of the preset output voltage. (Methods
for obtaining adjustable output voltages are shown in Section 3.)
For the floating regulators, the range of output voltages that can be obtained
with the regulator.
* Indicates that the maximum obtainable output voltage is dependent only on
the characteristics of the external pass element.
157
Maximum Output Current (10 max)
Absolute maximum output current that can be obtained without damaging regulator. (Methods for obtaining increased output current are shown in Section 3.)
* Indicates that the maximum obtainable output current is dependent only on
the characteristics of the external pass element.)
Input Voltage (Vin)
The range of allowable DC input voltage. This is an instantaneous value.
Exceeding maximum YIN could result in regulator damage, while dropping below
minimum value will cause loss of regulation.
Auxiliary Supply Voltage (Vaux )
The floating regulators require an additional dedicated voltage source which is
floating with respect to the output ground. The values given are the limits for this
auxiliary supply voltage.
Line Regulation (Regline)
Percent change in output voltage for a given change in input voltage. Test
specifications are given in the data sheets of Section 18.
Load Regulation (Regload)
Percent change in output voltage for a given change in output current. Test
specifications are given in the data sheets of Section 18.
Load Current Regulation
Percent change in output current for a given change in load voltage while
in the current regulation mode. Test specifications are given in the data sheets
of Section 18.
Typical Temperature Coefficient of Output Voltage (TC of Vol
Typical percent change in output voltage per degree Celsius change in junction
temperature.
Maximum Power Dissipation (Pnmax)
Maximum power which device can safely dissipate when case temperature is held
at + 25°C; and junction temperature is at its maximum value of + 125°C. For complete
thermal information, consult data sheets in Section 18. For heat sinking information, see
Section 15.
158
Package
Case 603C: lO-pin "TO-5" type metal can
Case 614: 9-pin "TO-66" type can
Case 632: 14-pin ceramic dual-in-line package
For detailed outline drawings of these case styles, consult Section 18.
TABLE 17-3
SPECIALTY REGULATORS
FLOATING REGULATORS
OUTPUT
VOLTAGE
(Vol
DEVICE
MIN
MC1566L'
0
MC1466L
0
.
.
MAX OUTPUT
CURRENT
.
.
MAX
loMAX
AUXILIARY
VOLTAGE
MIN
MAX
20V
3SV
21V
30V
CURRENT
LINE
LOAD
REGULATION REGULATION .REGULATION
TYPICAL
TC OFVo
.01%+1mV
.01%+1mV
.1%+1mA
±.OO6%JOC
.7SW
632
.03%+3mV
.03%+3mV
.1%+1mA
::t:.01%/OC
.7SW
632
PoMAX PACKAGE
TRACKING REGULATORS
OUTPUT
VOLTAGE
(Vol
INPUT
VOLTAGE
(Vinl
MIN
MAX
MAX OUTPUT
CURRENT
loMAX
MC1S66G'
±14.8V
±1S.2V
±100mA
±17V
±30V
.13%
.2%
±.OO6%fC
.8W
MC1566L'
±14.8V
±1S.2V
±100mA
±17V
±30V
.13%
.2%
±.OO6%fC
1.0W
MC1568R'
±14.8V
±1S.2V
±100mA
±17V
±30V
.13%
.2%
±.OO6%fC
2.4W
MC1468G
±14.SV
±1S.SV
±100mA
±17V
±30V
.13%
.2%
±.013%fC
.8W
MC1468L
±14.SV
±1S.SV
±100mA
±17V
±30V
.13%
.2%
±.013%/"C
1.0W
632
MC1468R
±14.SV
±1S.SV
±100mA
±17V
±30V
.13%
.2%
±.013%fC
2.4W
614
DEVICE
MIN
MAX
LINE
REGULATION
%Vo
LOAD
REGULATION
%Vo
TYPICAL
TC of Vo
PDMAX
PACKAGE
S03C
632
614
603C
Switching Regulator Control Circuits
Motorola offers a complete line of switching regulator I. e. s to meet the
various demands of the market. Table 17-4 lists devices offered along with key
parameters. For detailed specifications, refer to Section 18.
An explanation of the column headings shown in Table 17-4 follows:
Maximum Output Current (10 max)
This is the maximum output current capability of the switching control circuit
outputs. Most of the devices have dual push-pull outputs, except for the MC34060/
35060 and J.LA 78S40 devices which are single ended.
Supply Voltage (Vcc) minimax
Minimum applied voltage to Vee in which normal operation occurs. Maximum applied voltage to Vee, beyond which damage to the I.e. can occur. The
TL495 has an internal 39 volt zener and therefore can be operated from supplies
greater than 40 volts with a series current limiting resistor. For detail specifications, refer to Section 18.
Oscillator Frequency (fo)
The range in which the oscillator will operate to effectively drive the internal
logic and outputs.
159
Package
Case
Case
Case
Case
Case
Case
620:
632:
646:
648:
701:
726:
I6-pin
I4-pin
14-pin
I6-pin
I8-pin
I8-pin
ceramic dual-in-line package
ceramic dual-in-line package
plastic dual-in-line package
plastic dual-in-line package
plastic dual-in-line package
ceramic dual-in-line package
TABLE 17·4
SWITCHING REGULATOR CONTROL CIRCUITS
vee
I()
rnA
fo
kHz
Volts
Device
Max
Min
Max
Min
Max
Number
Suffix
40
10
30
2.0
100
MC3420
P
TA
"C
o to
+ 70
L
250'
7.0
40
1.0
300
MC3520
L
MC34060
P
250
7.0
40
1.0
300
L
TL494
CN
o to
+ 70
o to
+ 70
MJ
>40
1.0
300
TL495
CN
-25to +.85
±400
±200
1500
8
8
8
5
40
40
40
40
0.1
0.1
0.001
1
400
400
400
40
632
648
648
620
-55 to + 125
o to
+70
CJ
±400
646
620
IJ
250
620
632
55 to +125
CJ
IN
648
620
- 55 to + 125
L
MC35060
Ca.e
620
707
726
IN
-25 to +85
707
IJ
-25 to +85
726
SG3525A
N
0" to +70
648
SG3525A
J
o to
620
SG2525A
N
SG2525A
J
SG1525A
J
SG3527A
N
SG3527A
J
SG2527A
N
SG2527A
J
SG1527A
J
SG3526
N
SG3526
J
SG2526
N
SG2526
J
SG1526
J
iJA7SS40
PC
iJA7SS40
DC
iJA7SS40
OM
"Single output device
""Internal 39 V zener for <40 volt operation
160
+70
-40 to +85
648
620
-55to +125
o to
+ 70
620
648
620
-40 to +85
648
620
-55 to +125
o to
+ 70
620
707
726
-40 to +85
707
726
-55 to + 125
o to
+70
726
648
620
-55 to + 125
SECTION 18
REGULATOR DATA SBEETS
M
MOTOROLA
SEMICONDUCTORS
Product Prevle
Y
MOTOROLA
SEMICONDUCTORS
CONTRO~ CtR~I~SOOULA TION
SWITCHMODE PULSE WIO
161
----~------
®
LMI09
tM209
tM309
MOTOROLA
POSITIVE
VOLTAGE REGULATOR
MONOLITHIC POSITIVE THREE - TERMINAL
FIXED VOLTAGE REGULATOR
A versatile positive fixed +5.0-volt regulator designed for easy
application as on on-card, local voltage regulator for digital logic
systems. Current limiting and thermal shutdown are provided to
make the units extremely rugged.
In most applications only one external component, a capacitor,
is required in conjunction with the LM109 Series devices.
Even
this component may be omitted if the power-supply filter is not 10'
cated an appreciable distance from the regulator.
KSUFFIX
METAL PACKAGE
• High Maximum Output Current - Over 1.0 Ampere in TO·3 type
Package - Over 200 mA in TO-39 type Package.
CASE 1
(TO-3 Type)
• Minimum External Components Required
0
Output
2
• Internal Short-Circuit Protection
Input
• I nternal Thermal Overload Protection
1 0
0
3
Ground
• Excellent Line and Load Transient Rejection
(BOTTOM VIEW)
H SUFFIX
• Designed for Use with Popular MDTL and MTTL Logic
METAL PACKAGE
CASE 79
(TO·39)
QRDERING INFORMATION
Device
r--~---t--------'----""'--1--____. - . Output
I
Ground
6.3V
• Required if regulator is located an appreciable
distance from power supply filter.
Although no output capacitor is needed for
stability. it does improve transient response.
162
LM109, LM209, LM309
MAXIMUM RATINGS
Symbol
Value
Unit
I nput Voltage
Vin
35
Vdc
Power Dissipation
Po
Junction Temperature Range
TJ
Rating
Internally Limited
°C
-55 to +150
-55to+150
LM109
LM209
LM309
o to +125
Storage Temperature Range
Lead Temperature
(soldering, t = 60s)
T stg
-65 to +150
oC
TS
300
°C
ELECTRICAL CHARACTERISTICS
CD
LM109/LM209
Symbol
Characteristic
Output Voltage (TJ - +25 0 C)
Va
Input Regulation (TJ- +2SoC)
LM309
®
Min
Typ
Max
Min
Typ
Max
Unit
4.7
5.05
5.3
4.8
5.05
5.2
40
50
-
4.0
50
Vdc
mV
50
100
-
50
100
20
50
-
5.25
Vdc
10
mAde
Reg ln
-
70~Vln~25V
Load RegulatIOn
nJ
- +2SoC)
mV
Regload
Case 11-01 (type TO-3) 5 0 mA
~
IO~ 1 SA
Case 79·02 ITO-39 I 50 mA';:; '0 ~ 05A
Output Voltage Range
20
50
...
-
5.4
475
5.2
10
-
05
-
46
Va
7 0 V ~ V In ~ 25 V
-< 'max' P
I
125
150
FIGURE 6 - PEAK OUTPUT CURRENT (K PACKAGE)
I
IL
75
100
TA, AMBIENT TEMPERATURE (DC)
50
j---
~EATSINK -
t---,
2.0
500 mA
:2
1--
,...r:-
--
=>
a
-..~
--
~
- --
t--
1.0
~
~
r-:::::: ~
-55 DC -
1
~
~
Vo
TA
TA =+25 0 C
~
TA
TA
~+125DC
~+150DC-
I
4.5 V
10-2
10
100
1.0 k
10 k
f, FREOUENCY (Hz)
100 k
5.0
1.0 M
10
FIGURE 7 - PEAK OUTPUT CURRENT (H PACKAGE)
100
3.0
(
~
~
~
~
~
2.0
I
f-
~
~
!;
a
9
1.0
If
--r---- r--
...
r--
VD~4.5V
5.0
10
15
-------- -- ---- --
~
--
Y0..
/
~
BO
I:
...::.
z
~
......
-
a
60
35
~
+25 DC
Q.
Q.
"' 40
TA ~ +ll5 DC
TA Q I50 DC -
I
40
40
TA
~I -55 DC
-
T
w
~
.-- ~
1~
~
TA
35
TA
45
+150 DC...-"
=s
"V in ~ 3.0 Vp·p
L
~
~ "\
IL~200mA
-
~ ~25DC
~ :-...
TA~+125DC2~
B
UJ
TA ~ -5~DC
-:::: ~
20
30
25
Vin, INPUT VOLTAGE (V)
20
25
30
Vin, INPUT VOLTAGE (V)
FIGURE 8 - RIPPLE REJECTION
4.0
5
15
~
"\
J
20
10
45
100
1.0 k
10 k
f, FREOUENCY (Hz)
164
100 k
1.0 M
LM109, LM209, LM309
TYPICAL CHARACTERISTICS (continued)
FIGURE 10 - DROPOUT CHARACTERISTIC
(KPACKAGE)
FIGURE 9 - DROPOUT VOLTAGE
-----
2.5
-
:;
:; 2.0
., """:-
~
6.0
LMloo
andLM209
IL °
co
'"
5~O mA'
.,
:;
/'
~ 5.0
41
ii'
I-
~
TA ° 150 0 C "/,
~ 4.5 -TAo+125 0 C ---
IL"20m!>.
1
1 11 "°
I
+25
+50
+75 +100 +125
TJ. JUNCTION TEMPERATURE laC)
4.0
."
6.0
....
r----..
.....
~
'.'
D
.'
ii'
"'" 'x .'.
t;
o
i-----'-
LMI09
and
. LM209
IONLY
9.0
CL = 0
....... r-.
....
;
IL ° 20 rnA
I
0.01
4.8
-75
-50
-25
+25
+50
+75
+100 +125
TJ. JUNCTION TEMPERATURE laC)
10
+150 +175
100
FIGURE 14 - QUIESCENT CURRENT
I
LM109
and
LMZ09
IL0200mA
';'j
60
10 k
1.0 k
t. FREQUENCY 1Hz)
FIGURE 13 - QUIESCENT CURRENT
6.5
ONLY
j
I-
~
'"
'"=>
u
8.0
7.0
Vm.INPUTVOLTAGEIV)
~M~~
;:: 5.0
I-
YII
LM109
'"--...._OUTPUT
RI
300
1%
' - - - - - - - 4....._0UTPUT
'OETERMINES OUTPUT CURRENT.
FIGURE 18 - 5.0 VOLT, 4.0-AMPERE TRANSISTOR
FIGURE 17 - 5.0·VOLT, 3.0·AMPERE REGULATOR
(with plastic boost transistor)
(with plastic Darlington boost transistor)
MJE1090 OR EaUIV
,...-------,
lOV .......o-;.,
MJE370 0 R EaUIV
10 V .......-"v'lllr-oj(
I
I
47
%W
2n
8W
FIGURE 20 - 5.0-VOLT, 10-AMPERE REGULATOR
(with Short-Circuit Current Limiting for
FIGURE 19 - 5.0·VOL T, 10-AMPERE REGULATOR
Safe-Area Protection of pass transistors)
O.I.5W
MJ2955 OR EQUIV
10V ......- - - o j (
10
%W
5.0 V
O·IOA
30 V(max)
~~~~~~~~~~~.
10 V(minl
2N6049
OR EaUIV
166
@
LM117
LM217
LM317
MOTOROLA
3-TERMINAL ADJUSTABLE
OUTPUT POSITIVE VOLTAGE REGULATOR
The LM117/217/317 are adjustable 3-terminal positive voltage
regulators capable of supplying in excess of 1.5 A over an output
voltage range of 1.2 V to 37 V. These voltage regulators are exceptionally easy to use and require only two external resistors to set the
output voltage. Further, they employ internal current limiting,
thermal shutdown and safe area compensation, making them essentially blow-out proof.
The LM 117 series serve a wide variety of applications including
local, on card regulation. This device also makes an especially
simple adjustable switching regulator, a programmable output
regulator, or by connecting a fixed resistor between the adjustment
and output, the LM 117 series can be used as a precision current
regulator.
•
Output Current in Excess of 1.5 Ampere in TO-3 and TO-220
Packages
•
Output Current in Excess of 0.5 Ampere in TO-39 Package
•
Output Adjustable between 1.2 V and 37 V
•
Internal Thermal Overload Protection
•
Internal Short-Circuit Current Limiting Constant with Temperature
•
Output Transistor Safe-area Compensation
•
Floating Operation for High Voltage Applications
•
Standard 3-lead Transistor Packages
•
Eliminates Stocking Many Fixed Voltages
3-TERMINAL
ADJUSTABLE POSITIVE
VOLTAGE REGULATOR
SILICON MONOLITHIC
INTEGRATED CIRCUIT
K SUFFIX
METAL PACKAGE
CASE 1
(TO-3 Type)
Pins 1 and 2 electrically isolated from case,
Case is third electrical connection.
T SUFFIX
PLASTIC PACKAGE
CASE 221A
ITO-220)
Pin 1
Pin 2
Adjust
V out
Pin 3
Heatsink surface connected
to Pin 2
STANDARD APPLICATION
v out
V'n
LM117
H SUFFIX
.
'Adj
1
;, AI
<
Adjust
240
..
METAL PACKAGE
CASE 79
(TO·39i
(Bottom View)
-;; + Co
~
1 ~F
;::;::: Cin
0.1 J.lF
/.
~
Pin 1 Vin
Pin 2 Adjust
Pin 3 Vout
2
--
ORDEAING INFORMATION
«- "" Cin is required if regulator is located an appreciable distance from power
supply filter.
** = Co is not needed for stability. however it does improve transient
response.
V out : 1.25 V (1 + A2) + IAdj A2
AI
Since IAdj is controlled to lass than 100 J.l.A. the error associated with this
term is negligible in most applications
167
Device
LMl17H
LMl17K
LM217H
LM217K
LM317H
LM317K
LM317T
Temperature Range
TJ:
TJ:
TJ:
TJ :
TJ:
TJ:
TJ:
-55°C to +150 0 C
-55°C to +150 0 C
-25°C to +150 0 C
-25°C to +150 0 C
OOC to +1250 C
OOC to +1250 C
OOC to +125 0 C
Package
Metal Can
Metal Power
Metal Can
Metal Power
Metal Can
Metal Power
Plastic Power
LM117, LM217, LM317
MAXIMUM RATINGS
Rating
Symbol
Value
Unit
VI-VO
40
Vdc
Power Dissipation
Po
Internally
Operating Junction Temperature Range
TJ
Input-Output Voltage Differential
Limited
°c
LM117
LM217
LM317
-55 to +150
-25 to +150
o to +125
T stg
Storage Temperature Range
-65 to +150
°c
~ 5 V; 10 ~ 0.5 A for K and T packages; 10 ~ 0.1 A for H package;
TJ = Tlow to Thigh [see Note 1]; 'max and Pmax per Note 2; unless otherwise specified.)
ELECTRICAL CHARACTERISTICS IVI - Vo
Figure
Symbol
Line Regulation INote 3)
TA ~ 25 0 C, 3 V <; VI - Vo <; 40 V
1
Regline
Load Regulation (Note 3)
2
Characteristic
3
IAdj
1,2
.c.IAdj
Reference Voltage INote 4)
3 V <; VI - Vo <; 40 V
10 mA <; 10 <; Imax , Po <; Pmax
Line Regulation INote 3)
3V<;VI- VO<;40V
3
Vref
1
Reglin~
Load Regulation (Note 3)
10 mA <; 10 <; Imax
2
Adjustment Pin Current
10 rnA ~ 'L"';;; 'max. PD ~ Pmax
3
TS
Minimum Load Current to
3
ILmin
Maintain Regulation (VI - Vo ~ 40 V)
-
Ripple Rejection, Vo - 10 V, f - 120 Hz (Note 5)
Without CAOJ
CAOJ ~ 10 IJ.F
4
Long Term Stability, T J - Thigh (Note 6)
T A ~ 25 0 C for Endpoint Measurements
3
Thermal Resistance Junction to Case
H Package (TO-39)
K Package (TO-3)
T Package ITO-220)
-
NOTES:
Max
-
0.Q1
0.04
-
5
0.1
25
0.5
%VO
50
100
IJ.A
Unit
0.01
0.02
-
5
0.1
15
0.3
50
100
-
-
mV
IJ.A
0.2
5
-
0.2
5
V
1.20
1.25
1.30
1.20
1.25
1.30
-
0.02
0.05
-
0.02
0.07
-
20
0.3
50
1
20
0.3
70
1.5
mV
%VO
0.7
-
-
0.7
-
%VO
-
3.5
5
-
3.5
10
%/V
mA
A
'max
VI- Vo <; 15 V, Po <; Pmax
K and T Packages
H Package
VI -Vo ~40V,PO<; Pmax , TA ~250C
K and T Packages
H Package
RMS Noise, % of Vo
TA ~ 250 C, 10 Hz <; f <; 10 KHz
LM317
Typ
Regload
Temperature Stability ITIow <; T J <; Thigh)
3
Min
%/V
-
-
Vo <; 5 V
VO;' 5 V
Maximum Output Current
LM1t7/217
Typ
Max
Regload
T A ~ 25 0 C, 10 mA <; 10 <; Imax
Vo <; 5 V
VO;' 5 V
Adjustment Pin Current Change
2.5 V <; VI - Vo <; 40 V
Min
1.5
0.5
2.2
0.8
-
-
0.15
-
0.4
0.07
-
0.003
-
-
0.003
-
65
80
-
-
66
65
80
-
0.3
1
-
0.3
1
12
2.3
15
3
-
15
3
-
-
12
2.3
5
-
1.5
0.5
2.2
0.8
-
0.25
-
0.4
0.07
-
-
N
%VO
dB
RR
66
S
%/1.0k Hrs
-
ROJC
II lTiow ~ -550 C for LMl17
Thigh = +1500C for LMl17
= -25 0C for LM217
= +1500 C for LM217
= OoC for LM317
= +1250 C for LM317
(2) Imax = 1.5 A for K ITO-3) and T ITO-220) Packages
~ 0.5 A for H (T0-39) Package
Pmax = 20 W for K (T0-3) and T ITO-220) Packages
~ 2 W for H (T0-39) Package
(3) Load and line regulation are specified at constant
junction temperature. Changes in Vo due to heating
168
°C/W
-
-
-
effects must be taken into account separately. Pulse
testing with low duty cycle is used.
(4) Selected devices with tightened toJerance reference
voltage available.
(5) CADJ, when used, is connected between the
adjustment pin and ground.
(6) Since Long Term Stability cannot be meesured on
each device before shipment. this specification is an
engineering estimate of average stability from lot to
lot,
LM117, LM217, LM317
SCHEMATIC DIAGRAM
0.1
k-~--~----~--~~~~~~-4--~--~--~----~-------4--~--------------~~--~----0
k------------------------------------~O
FIGURE 1 - LINE REGULATION AND t>IAdj/LINE TEST CIRCUIT
Vee
Line Regulation (%/V)
0=-
VOH_~~
VOL
V out
LM117
Adjust
240
1%
0.1 MF
* Pulse Testing Required:
1 % Duty Cycle
is suggested.
169
X 100
Vout
Ad) ust
LM117, LM217, LM317
FIGURE 2 - LOAD REGULATION AND Ll.IAdj/LOAD TEST CIRCUIT
L.oad Regulation (mV) ==
Vo
Va
(min. Load) -
(max. Load)
Load Regulation (%Vo);::: Vo (min. Load) - Vo (ma)(. Loadl x 100 t
Vo
Vout
LM117
iVO (min. Load)
U Vo
(min. Load)
(max. Load)
IL
RL
(max. Load)
240
1%
Adjust
RL
(min. Load)
+
0.1 j,lF
*'I'ulse Testing Required:
1 % Duty Cycle is suggested.
FIGURE 3 - STANDARD TEST CIRCUIT
V out
LM117
240
1%
RL
II'F
e
I
I
I
I
I
l
To Calculate R2:
Pulse Testing Required:
1 % Duty Cycle is suggested.
Va = ISET R2
+ 1.250 V
Assume 'SET"" 5.25 rnA
FIGURE 4 - RIPPLE REJECTION TEST CIRCUIT
24 V-:-("'\
14 V _--,__
'.
V
V out
Viii
Va = 10 V
LM117
f"'" 120 Hz
Adjust
Cin
240
1%
Rl
I
I
Dl'
~~
RL
lN4002
+
;:::r: 0.1 j,lF
Co;::r: 1 I'F
I
1.65 K
1%
R2
--'--
1+
CADJ
;~.:
10 /JF
1
1
.
01 Discharges CADJ
170
If
Output
IS
Shorted to Ground.
Va
LM117, LM217, LM317
FIGURE 5 - LOAD REGULATION
£w
FIGURE 6 - CURRENT LIMIT
0.4
'"z
«
0.2
'"
u
-
w
«
'"
'::; -0.2
0
>
I-
IL=0.5A
1---
r-- -.......
IL = 1.5 A -.....
-0.4
~
!;
-0.6
0
6
-
I- VI =15V
Vo 110 V
_
f------
TJ = 25°C
I
-
I
TJ = 150°C ...
-I-~
- .=t:--' .....
r-.......
"
I
~
TJ=-550C
~-
r-:::..: ..:::::- --
>
25
50
75
100
TJ. JUNCTION TEMPERATURE 1°C)
125
1.5
..;;..
FIGURE 9 - TEMPERATURE STABILITY
;;;- 1.250
""'"'::;
o
>
~ 1.240
;;;
-25
~
50
75
100
25
TJ . JUNCTION TEMPERATURE 1°C)
--
125
150
FIGURE 10 - MINIMUM OPERATING CURRENT
5.0
4.5
----
TJ = -55°C
---
~
-.........
.5
I--
-.....
;;;
~
~
4.0
. , / TJ = 25°C
3.5
/-:,: ~ J
3.0
.,.2- ~
~ 2.5
I-
~
~
--
2.0
t:l
:=i 1.5
'"i; 1.230
'"_Ct:J 1.0 ~ ~-
>~
0.5
1.2.20
-75
-50
>-
1.260
:>
~200mA
IL =20mA
>°1.0
I
-75
150
--
-~
~
-25
-.
r--~
I-
I
-;7
___ IL = 500 mA
~
'"
........
IL = 1.0 A
~
I-
0
._---
~.
IL = 1 5 A
'"
0
6V O = 100mV- 1---
---1--- t - -
2.5
w
""'::;
40
-50
-25
25
50
75
100
125
o
150
TJ. JUNCTION TEMPERATURE 1°C)
~~
1-
,. T =150oC-
V
I
o
10
20
30
40
VI - VO.INPUT - OUTPUT VOLTAGE DIFFERENTIAL IVdc)
171
LM117, LM217, LM317
FIGURE 11 - RIPPLE REJECTION VS OUTPUT VOLTAGE
100
FIGURE 12 - RIPPLE REJECTION VS, OUTPUT CURRENT
,I
,I
CAOJ -10~F
120
'"...
'"
80
.......
0
-=
'-'
60
r--
~
'"
W
~
a:
a!
'"
40
f--
r--
o
:s
z
WITHOUT CAOJ
10
CAOJ = 10~F
t
80
W
'"
60
;:
40
r---
20
I----
~
~
f--
",'
'"
I
o
100
o
VI -Vr 5V
I L =50mA
f= 120 Hz
TJ = 25°C
f-20
-
OJ
30
15
20
25
VO' OUTPUT VOLTAGE (V)
VI "15V
Vo -10 V
f-120Hz
TJ = 25°C
-1111
o
0.01
35
.....
WITHOUT CAOJ
0.1
10 , OUTPUT CURRENT (A)
10
FIGURE 14 - OUTPUT IMPEDANCE
FIGURE 13 - RIPPLE REJECTION VS. FREQUENCY
100
~
.-...
80
--
~ -500mA
1= 15V V ·10V
TJ=250C -
/
z
/
/ ...........
1"u
-= 60
;]
V
~ \
'"...
~\
it 40
0
W
W
\
;:
"'.
a:
20
WITHOUT CAOJ
J
J
o
r-
rWITHOUT CADJ
\.
CAOJ = 10
'\,J
~F
"-.1
10-3
10
100
lK
10K
lOOK
1M
f, FREQUENCY (Hz)
10
10M
W
1.5
~> 1.0
0-
>z
... 9 O.5
i~
:0>
0
,0
0
-0. 5
... -
OW
>
<3
W
t:>
1.0
>w
-J
0-
!;~
...
25 IJ.F, CADJ > 10 IJ.F).
Diode Dl prevents Co from discharging thru the I.C.
during an input short circuit. Diode D2 protects against
capacitor CADJ discharging through the I.C. during an
output short circuit. The combination of diodes Dl and
D2 prevents CADJ from discharging through the I.C.
during an input short circuit.
FIGURE 17 - BASIC CIRCUIT CONFIGURATION
LM117
-1
! v out
II----O-(-+
>-R1
Vref
Adjus,
--
\
l'PROG
FIGURE 18 - VOLTAGE REGULATOR WITH
PROTECTION DIODES
V out
lAd]
R2
1
D1
Vref"'" 1.25 V TYPICAL
IN4002
LOAD REGULATION
The LM 117 is capable of providing extremely good
load regUlation, but a few precautions are needed to
obtain maximum performance. For best performance, the
programming resistor (R 1) should be connected as close
to the regulator as possible to minimize line drops which
effectively appear in series with the reference, thereby
degrading regulation_ The ground end of R2 can be
returned near the load ground to provide remote ground
sensing and improve load regulation_
173
LM117, LM217, LM317
FIGURE 19 - "LABORATORY" POWER SUPPLY WITH ADJUSTABLE
CURRENT LIMIT AND OUTPUT VOLTAGE
IN4002
V out l
V I N __....-<:>-----1
Rse
f--o-.......- - -.....- _
Vo
32 to 40 V
II'F
Tantalum
Dl
IN4001
IN4001
lK
Current
D2
Limit
Adjust
°1
2N3822
OUTPUT RANGE:
O';;;;VO"';;;;25V
~10V
Diodes 01 and 02 and transistor 02 are added to allow adjustment
of output voltage to 0 volts.
O';;';;:IO~1.2A
°2
2N5640
06 protects both LM117's during an input short circuit.
~10
FIGURE 21 - 5 V ELECTRONIC SHUT DOWN REGULATOR
FIGURE 20 - ADJUSTABLE CURRENT LIMITER
V out
V
R1
1.25
V out
+
Dl
I1.0IlF
IN4001
*.
To provide current limiting of '0
to the svstem ground, the source of
the FET must be tied to a negative
100
D2
Adjust
0--...........-...]
IN4001
voltage below -1.25 V.
TTL
Control
720
;a. Vref
R
2
Rl
1 K
IDSS
~
Vref
lOmax + lOSS
Vo
8VDSS + 1.25 V + VSS
ILmin - IDSS
10
1.5 A
As shown 0
10
1 A
<
<
<
<
Minimum V out "'" 1.25 V
<
01 protects the device during an input short circuit.
FIGURE 23 - CURRENT REGULATOR
FIGURE 22 - SLOW TURN·ON REGULATOR
Vin
LMI17
Adjust
~
I
V out
Rl
I
~
Vraf
lout ~ (AI)
+
IAdj
'" 1.25 V
Rl
10 rnA <; lout.s;;: 1.5 A
174
'out
----+
LMl17L
LM217L
LM317L
@ MOTOROLA
3-TERMINAL ADJUSTABLE
OUTPUT POSITIVE VOLTAGE REGULATOR
The LMl17L/217L/317L are adjustable 3-terminal positive
voltage regulators capable of supplying in excess of 100 mA over an
output voltage range of 1.2 V to 37 V. These voltage regulators are
exceptionally easy to use and require only two external resistors
to set the output voltage. Further, they employ internal current
limiting, thermal shutdown and safe area compensation, making
them essentially blow-out proof.
The LMl17L series serves a wide variety of applications including
local, on card regulation. This device also makes an especially
simple adjustable switching regulator, a programmable output
regulator, or by connecting a fixed resistor between the adjustment
and output, the LMl17L series can be used as a precision current
regulator.
•
Output Current in Excess of 100 mA
•
Output Adjustable Between 1_2 V and 37 V
•
Internal Thermal Overload Protection
•
Internal Short-Circuit Current Limiting
•
Output Transistor Safe-Area Compensation
Floating Operation for High Voltage Applications
•
Standard 3-Lead Transistor Packages
•
Eliminates Stocking Many Fixed Voltages
STANDARD APPLICATION
'n
;::
1
CASE 29
TO 92
PLASTIC PACKAGE
(LM317L only)
Pin 1
Pin 2
Adjust
Vout
Pin 3
Yin
H SUFFIX
v out
'Ad]
Z SUFFIX
METAL PACKAGE
CASE 79
LM117L
----
(TO-39l
240
Adjust
*
SILICON MONOLITHIC
INTEGRATED CIRCUIT
"2 3
•
V
LOW-CURRENT
3-TERMINAL
ADJUSTABLE POSITIVE
VOLTAGE REGULATOR
C in
f"
0.1 }.iF
~
~~*
::::r--
(Bottom View)
1:F
/<
Pin 1
V in
Pin 2
Adjust
Pin3
V out
* ;:
* * '"
Cin is required if regulator is located an appreciable distance from power
supply filter.
Co is not needed for stability, however it does improve transient
response.
V out "" 1.25 V (1 +
R2
R,) + IAdj
R2
Since 'Adj is controlled to less than 100 /J.A, the error associated with this
term is negligible in most applications
175
ORDERING INFORMATION
Device
Temperature Range
Package
LM117LH
TJ"" -55°C to +150 0 C
Metal Can
LM217LH
TJ" -25°C to +150 0 C
Metal Can
LM317LH
T J - OOC to + 125°C
Metal Can
LM317LZ
T J - OOC to + 125°C
I")lastlc
LM117L, LM217L, LM317L
MAXIMUM RATINGS
Rating
Input-Output Voltage Oifferential
Symbol
Value
Unit
VI-Va
40
Vdc
Po
Internally Limited
TJ
-55 to +150
-25 to +150
to +125
°C
Tstg
-65 to +150
°C
Power Dissipation
Operating Junction Temperature Range
LMl17L
LM217L
LM317L
Storage Temperature Range
o
ELECTRICAL CHARACTERISTICS
(VI- Va 05 V, 10 0 40 mA; TJ 0 Tlow to Thigh [see Note 1]; Imax and Pmax per Note 2; unless otherwise specified.)
Characteristic
Figure
Symbol
Line Regulation (Note 3)
TA 0 25°C, 3 V 0( VI-Va 0( 40 V
1
Regline
Load Regulation (Note 3), TA 0 25°C
5 mAo( lao( Imax - LM117L1217L
10 mA 0( 10 0( Imax - LM317L
Va 0( 5V
VO~ 5V
2
Regload
Adjustment Pin Current
3
lAd)
Min
LM 117L121 7L
Typ
Max
Min
LM317L
Typ
Max
Unit
%/V
-
0.01
002
-
001
0.04
-
5
0.1
15
0.3
-
5
01
25
0.5
mV
%VO
-
50
100
-
50
100
fJA
._--
-~---~
Adjustment Pin Current Change
2.5 V 0( VI-VO 0( 40 V, Po 0( Pmax
5 mA 0( 100( Imax - LM117L/217L
10 mA 0( 100( Imax - LM317L
1.2
Reference Voltage (Note 4)
3 V 0( VI-Va 0( 40 V, Po 0( Pmax
5 mA 0( 100( Imax - LMl17L1217L
10 mA 0( 100( Imax - LM317L
3
Line RegulatIOn (Note 3)
3 V 0( VI-VO 0( 40 V
1
Load Regulation (Note 31
5 mA 0( 100( Imax - LMl17L/217L
10 mAo( lao( Imax- LM317L
VOo( 5V
VO~ 5V
2
Temperature Stability (Tlow 0( TJ 0( Thigh)
3
TS
MInimum Load Current to
Maintain Regulation (VI-Va 0 40 VI
3
ILmin
Maximum Output Current
3
61Ad)
1.25
1.30
1 20
125
130
%/V
RegIme
0.02
0.05
-
002
007
-
20
0.3
50
1
-
20
03
70
15
-
0.7
-
-
0.7
-
3.5
5
-
3.5
200
200
-
Long Term Stability, TJ 0 Thigh (Note 61
TA 0 25°C for Endpoint Measurements
3
Thermal Resistance Junction to Case
H Package (TO-39)
Z Package (TO-92)
-
- -- - -
----'----
%VO
10
-- - A
Imax
-
100
1005
200
200
-
-
50
20
-
-
50
20
-
-
0003
-
-
0.003
-
80
80
-
60
-
80
80
-
-
0.3
1
-
0.3
1
-
40
-
-
40
160
-
~
-
N
O/OVO
RR
dB
66
-
S
%/1.0 k
Hrs.
°C/W
ROJC
=+150°C for LM117L
=+150oC for LM217L
:::: +125°C for LM317L
mV
%VO
mA
-
4
. -.
Regload
100
100
Ripple Rejection (Note 5)
Vo 0 1.25 V, f 0 120 Hz
CAOJ 010 I'F Va 010.0 V
(21 Imax 0 100 mA
Pmax :::: 2 W for H (TO-39) Package
= 625 mW for Z (TQ-921 Package
5
V
-
Thigh
02
_.
-
-
-25°C for LM217L
5
-
Vrel
1.20
RMS Noise, % 01 Vo
TA 0 25°C, 10Hz 0( 10( 10kHz
ooe for LM317L
0.2
--
VI-VO 0( 20 V, Po 0( Pmax H Package
VI-Va 0( 6.25 V, Po 0( Pmax , Z Package
VI-VO 0 40 V, Po 0( Pmax , TA 0 25°C
H Package
Z Package
NOTES:
(11 Tlow 0 -55°C for LMl17L
fJA
-
-
(3) Load and line regulation are specIfied at constant JunctIon temperature
Changes In Vo due to heating effects must be taken into account
separately. Pulse testing with low duty cycle is used.
(4) Selected devices wIth tightened tolerance reference voltage avaIlable
(5) CADJ' when used, is connected between the adjustment pin and
ground.
(6) Since Long Term Stability cannot be measured on each devIce before
shipment, this speCificc:tlon is an engineering estimate of average
stability from lot to lot.
176
LM117L, LM217L, LM317L
SCHEMATIC DIAGRAM
VINo---._-----.------~~------~------------._~~------~----~--~----~--_,
6.8 V
6.8 V
350
130
2.5
2 k
6 k
' -.....o--Jvv\r-...""'Ar-----Q Adjust
FIGURE 1 - LINE REGULATION AND AIAdj/LiNE TEST CIRCUIT
Vcc
Line Regulation (%/V) =
~
VOH--VOL
----X
~IH
VIL
VOL
100
.JL,.0H
VOL
V out
Vin
LMl17L
Adjust
Cl n
::;.':::
O.lIlF
R2
1%
1 % Duty Cycle
Is suggested.
240
1%
RL
+
Co;;:!::;:: 11lF
IAdj
"" Pulse Testing Required:
Rl :
-=--
177
LM117L, LM217L, LM317L
FIGURE 2 - LOAD REGULATION AND 41Adj/LOAD TEST CIRCUIT
Load Regulation (mV) • Vo (min. Load) - Vo (max. Load)
Load Regulation ("VO) _ Vo (min. Load) - Vo (mo •• Load) X 100-' ,VO (min. Load)
V out
Vo (max. Load)
RL
(max. Lqad)
240
Adjult
1"
RL
(min. Load)
+
O.IIJ.F
*
U
Vo (min. Load)
IL
LM117L
1 IJ.F
Pul.e Testing Required:
1" Duty f!:ycle II suggested.
FIGURE 3 - STANDARD TEST CIRCUIT
Vout
LMI17L
240
1%
O.IIJ.F
To Calculate R2:
Vo = ISET R2 + 1.250 V
Allum. ISET = 5.25 mA
Pulse Testing Required:
1 % Duty Cycle ISluggested.
FIGURE 4 - RIPPLE REJECTION TEST CIRCUIT
14.30V-(\
.
4.30V---V
Vout
Vin
Vo = 1.25 V-
LM117L
f-120 Hz
Adjust
Rl
<
240
1%
°1"
~~
RL
lN4002
+
Cln ;;:~ O.IIJ.F
Co;;: ~ llJ.F
1.65 K
R2
1%
-~
1+
CAOJ
;i~
10 IJ.F
1
1
"
0, Discharges CADJ If Output IS Shorted to,Ground.
"·CADJ provide. an AC Ground to the Adjust Pin.
178
Vo
LM117L, LM217L, LM317L
FIGURE 6 - RIPPLE REJECTION
FIGURE 5 - LOAD REGULATION
~
0.4
..'"
w
~
V)45V
0.2
/
'-'
w
!i
~
o
'".....w
-0. 6
'"
-1.0
f = 120 Hz
60 f---
'1
-25
25
50
75
100
TJ, JUNCTION TEMPERATURE (OC)
125
-50
150
FIGURE 7 - CURRENT LIMIT
-r--..... "'-
0.50
!S
!;;
-..... r-.....
~ 0.30
'"=>
'-'
!;;
" I'..
"
:= 0.20
TJ=15OOC
=>
o
o
- 0.10
o
o
r--.
" I'-..."
"
"
TJI"550C'---~
t-
3.5 -
TJ=25 0C - - TJ=1500C - - -
'"
a'"
3.0
-50
-
25
50
75
100
TJ,JUNCTION TEMPERATURE (OC)
125
150
I'-...
........
............
--- - ::~-:--....
IL -100mA
r-----..
--t......
-25
25
50
75
100
125
150
TJ, JUNCTION TEMPERATURE (OCI
FIGURE 10 - RIPPLE REJECTION versus FREQUENCY
°L
2.5
'-' 2.0
[ll
0.5
f-.-
0.5
50
90
15
~ 1.0
-.
........
10
30
40
20
VI- VO,INPUT - OUTPUT VOLTAGE DIFFERENTIAL (VOLTS)
_
:; 1.5
1
100
4.5
d
~
r-....
FIGURE 9 - MINIMUM OPERATING CURRENT
t-
-25
-.....
5.0
.§
--
FIGURE B - DROPOUT VOLTAGE
2. 5
TJ=250C
~ 0.40
"15
r--
--
Vo "10 V
V,n = 14t024V
50
-50
4.0
- - f---- _.- -
IL =40mA
r---
;0
~ -0.8
"""- r--
70
it
",-
---- -
.-
~
'-'
;;J
Vout "5V
IL" 5to 100mA
-0.4
t-
--
80
z
r-- Vin"10V
o
>
~
0
T
!:i -0.2
..g
I _
Vout "5V
IL"5t040mA_
,- ~ --::-....
~
,
...
~
~
.....
I-
/... '
Vin = 5V
\
0
\
\
10
10
20
30
40
10
Vl- VO,INPUT - OUTPUT VOLTAGE DIFFERENTIAL (VOLTS)
179
100
lK
±
1 Vpp
Vo = 1.25V
\
1'--
1
iL=40mA
.......
10K
100 K
1m
f, FREQUENCY (Hz)
_
-
LM117L, LM217L, LM317L
FIGURE 11 - TEMPERATURE STABILITY
FIGURE 12 - ADJUSTMENT PIN CURRENT
1.2110
I
>
·v
;;; 1.250
~
~
~ ......
1/
'"
$
5
"
Vin"4.2V
; 1.230 I - - VO'V",
IL" 5 mA
>
~
5
-25
25
50
75
100
TJ,JONCTION TEMPERATURE 10C)
125
150
-50
-25
0.4
-
0.2
-
1
-
0
25
50
75
100
TJ, JUNCTION TEMPERATURE 10C)
125
150
FIGURE 14 - OUTPUT NOISE
FIGURE 13 - LINE REGULATION
J
.1
Vin' 4.25 to 41.25 V
VO·V r.,
-IL=40mA
/
Bandwidth 100 Hz to 10 kHz
>
.3
10
'"
'"
~ -0.2
o
>
i -0.4
g -0.6
~
..
. ..,
1";:::-
5
-50
.
-==
~-
./'
r
1.220
~
I
10mA
I - - t-- ---IL"
--IL=loomA
r-- ..........
/
~ 1.240
£
i'"
.I
6.25 V
I - - t-- Vin'
VO"Vr.,
I--
-O.B
--
I-"""
c:~
V
./
B.O
'"o
z
-1.0
6.0
...-
V
" .V
>
!!!
/"
~
4. 0
-50
-25
0
25
50
75
100
TJ,JUNCTION TEMPERATURE 10C)
125
150
-50
FIGURE 15 - LINE TRANSIENT RESPONSE
..
~
0
~> 0.2
0
5
0
VO·1.25V
IL"20mA
TJ·250C
0'"
6°-0.1
1-0·3
~~ 100 i>
~'"
-J
i
10
20
t, TlMEljISj
-0,2
C 0
L I
0
0
~~
A
5
150
I"~t
C
,t
>z
~~ 0.1
~'/
"-
125
'"
0.3
0-
CL " I/tF
.1\
0
25
50
75
100
TJ,JUNCTION TEMPERATURE 10C)
FIGURE 16 - LOAD TRANSIENT RESPONSE
5
5
-25
.:~ 50
-::::I
.. 0
40
\
I~!
:t r--
\/
I
V " 15 V
V~ -IOV
~L "IOmA
J" 25 0C
-
~~L
I
'I
\ 1
10
180
1
,CL -0.3 I'F; CAOJ = lOP! -
20
t, TIME
30
l/t~
40
LM117L, LM217L, LM317L
APPLICA nONS INFORMA nON
BASIC CIRCUIT OPERATION
The LMl17L is a 3·terminal floating regulator. In
operation, the LMl17L develops and maintains a nominal
1.25 volt reference (V ref) between its output and adjust·
ment terminals. This reference voltage is converted to a
programming current (lPROG) by R 1 (see Figure 13),
and this constant current flows through R2 to ground.
The regulated output voltage is given by:
EXTERNAL CAPACITORS
A 0.1 }1F disc or 1 }1F tantalum input bypass capacitor
(Cin) is recommended to reduce the sensitivity to input
line impedance.
The adjustment terminal may be bypassed to ground to
improve ripple rejection. This capacitor (CADJ) prevents
ripple from being amplified as the output voltage is
increased. A 10 }1F capacitor should improve ripple
rejection about 15dB at 120 Hz in a 10 volt application.
Although the LM117L is stable with no output capaci·
tance, like any feedback circuit, certain values of external
capacitance can cause excessive ringing. An output capaci·
tance (Co) in the form of a 1 IJ.F tantalum or 25 }1F
aluminum electrolytic capacitor on the output swamps
this effect and insures stability.
R2
Vout = Vref (1 + Fil) + IAdj R2
Since the current from the adjustment terminal (IAdj)
represents an error term in the equation, the LM 117 L was
designed to control IAdj to less than 100}1A and keep it
constant. To do this, all quiescent operating current is
returned to the output terminal. This imposes the require·
ment for a minimum load ciJrrent. If the load current is
less than this minimum, the output voltage will rise.
Since the LM117L is a floating regulator, it is only the
voltage differential across the circuit which is important
to performance, and operation at high voltages with
respect to ground is possible.
PROTECTION DIODES
When external capacitors are used with any I.C. regu·
lator it is sometimes necessary to add protection diodes to
prevent the capacitors from discharging through low
current points into the regulator.
Figure 14 shows the LM117L with the recommended
protection diodes for output voltages in excess of 25 V 01
high capacitance values (Co> 10 IJ.F, CADJ > 5 j.1Fi.
Diode Dl prevents Co from discharging thru the I.C.
during an input short circuit. Diode D2 protects against
capacitor CADJ discharging through the I.C. during an
output short circuit. The combination of diodes Dl and
D2 prevents CADJ from discharging through the I.e.
durrng an Input short cirCUit.
FIGURE 17 - BASIC CIRCUIT CONFIGURATION
I
L M 11 7 L
v out
~r
jf------«>--------<+""'--"R
1
Vref
Adr
u
"
\
FIGURE 18 - VOLTAGE REGULATOR WITH
PROTECTION DIODES
lr PROG
V out
R2
1
V ref"" 1.25 V TYP1CAL
IN4002
LOAD REGULATION
The LM 117 L is capable of providing extremely good
load regulation, but a few precautions are needed to
obtain maximum performance. For best performance, the
programming resistor (R 1) should be connected as close
to the regulator as possible to minimize line drops which
effectively appear in series with the reference, thereby
degrading regulation. The ground end of R2 can be
returned near the load ground to provide remote ground
sensing and improve load regulation.
181
LM117L, LM217L, LM317L
FIGURE 19 - ADJUSTABLE CURRENT LIMITER
Vo
FIGURE 20 - 5 V ELECTRONIC SHUTDOWN REGULATOR
--.10
12.5 k
R2
500
·To provide current limiting of 10 to
the system ground, the source of the
V out
01
I
1N914
02
Adjust
1NS14
+
1 OIlF
.
0--.......----'
current limiting diode must be tied
to a negative voltage below -7.25 V.
>
A
2
TTL
720
lOSS
Control
1 K
Vret
1 N5314
Vref
A, ;::: lOmax + lOSS
Minimum V out "" 1 .25 V
Va < POV + 1.25 V + VSS
'Lmm - Ip< '0 < 100mA -Ip
As shown 0 < 10 < 95 rnA.
D, protects the deVice during an Input short CirCUit
FIGURE 22 - CURRENT REGULATOR
FIGURE 21 - SLOW TURN-DN REGULATOR
'out
------to
-'Adj
(V~~f
loutmax =
loutmin
=
+ lad; " 1.25 V
(R;:e~2)+
5 mA
182
)
<
lout
<
R1
ladj
100 mA
,,~
R, + R2
LMl17M
LM217M
LM317M
@ MOTOROLA
3-TERMINAL ADJUSTABLE
OUTPUT POSITIVE VOLTAGE REGULATOR
The LM117M/217M/317M are adjustable 3-terminal positive
voltage regulators capable of supplying in excess of 500 mA over an
output voltage range of 1.2 V to 37 V. These voltage regulators are
exceptionally easy to use and require only two external resistors to
set the output voltage. Further, they employ internal current
limiting, thermal shutdown and safe area compensation, making
them essentially blow-out proof.
The LM117M series serve a wide variety of applications including
local. on card regulation. This device also makes an especially
simple adjustable switching regulator, a programmable output
regulator, or by connecting a fixed resistor between the adjustment
and output, the LM117M series can be used as a precision current
regulator.
•
MEDIUM-CURRENT
3-TERMINAL
ADJUSTABLE POSITIVE
VOLTAGE REGULATOR
SILICON MONOLITHIC
INTEGRATED CIRCUIT
R SUFFIX
METAL PACKAGE
CASE 80-02
(TO-56 Type)
Output Current in Excess of 500 mA
•
Output Adjustable Between 1.2 V and 37 V
•
Internal Thermal Overload Protection
•
Internal Short-Circuit-Current Limiting
(Bottom View)
•
Output Transistor Safe-Area Compensation
•
Floating Operation for High Voltage Applications
•
Standard 3-Lead Transistor Packages
•
Eliminates Stocking Many Fixed Voltages
Pins 1 and'} electrically isolated from case.
Case is third electrical connection.
STANDARD APPLICATION
T SUFFIX
PLASTIC PACKAGE
v out
V 'n
LM117M
;::f:;
> R,
.
..
240
IAdil
Adjust
-;:; Co
C in
r--
0.1,uF
~
1
~F
~
Adjust
2
V out
Pin 3
Heatsink surface connected
to Pin 2
-~
*
**
Cin is required if regulator is located an appreciable distance from power
supply filter.
Co i. not needed for stability, however it does improve transient
r ••ponH.
VO::: 1.25 V (1
+
V in
R2
R.;'
")
+ ladj R2
Since ladj is controlled to less than 100 JJA. the error associated with this
term is negligi"ble in mo.t applications
183
ORDERING INFORMATION
Device
Temperature Range
LM117MR
LM217MR
LM317MR
LM317MT
TJ;:: -55°C to +15QoC
TJ -2SoC to +150°C
TJ - O°C to +125°C
TJ - O°C to +125°C
Package
Metal Power
Metal Power
Metal Power
Plastic Power
LM117M, LM217M, LM317M
MAXIMUM RATINGS
Rating
Input-Output Voltage Differential
Symbol
Value
Unit
VI-Va
40
Vdc
Po
Internally Limited
TJ
-55 to +150
-25 to +150
to +125
°C
Tstg
-65 to +150
°C
Power Dissipation
Operating Junction Temperature Range
LMl17M
LM217M
LM317M
Storage Temperature Range
o
ELECTRICAL CHARACTERISTICS
IVI - Va = 5 V, 10 = 0,1 A, TJ = Tlow to Thigh [see Note 1 j, Pm ax per Note 2, unless otherwise specll,ed )
Characteristic
Figure
Symbol
Line Regulation INote 3)
TA = 25°C, 3 V';; VI-Va';; 40 V
1
Regline
Load Regulation INote 3),
TA = 25°C, 10 mA';; 10';; 0 5 A
Va';; 5 V
Va? 5 V
2
Regload
Adjustment Pin Current
3
ladl
Adjustment Pin Current Change
2,5 V';; VI-Va';; 40 V,
10 mA';; IL';; 0.5 A, Po';; Pmax
1,2
6l ad,
Relerence Voltage INote 4)
3 V,;; VI-Va';; 40 V
10 mA';; 10';; 0.5 A, PO';; Pmax
3
Vrel
Line Regulation INote 3)
3 V';; VI-Va';; 40 V
1
Regime
Load Regulation INote 3)
10mA';;lo';;0.5A
Va';; 5 V
Va? 5 V
2
Temperature Stability ITlow';; TJ';; Thigh)
3
TS
Minimum Load Current to
Maintain Regulation lVI-Va = 40 V)
3
'Lmin
Maximum Output Current
3
RMS Noise, % 01 Va
TA = 25°C, 10Hz';; I';; 10 kHz
-
Ripple Rejection, Va = 10 V, I = 120 Hz
INote 5)
Without Cad,
4
3
Thermal Resistance Junction to Case
R Package ITO-66)
T Package ITO-220)
-
(2) Pmax
LM317M
Typ
Max
Unit
-
0.01
0.02
-
001
0,04
-
5
01
15
0,3
-
5
0.1
25
0.5
mV
%VO
-
50
100
-
50
100
"A
-
0.2
5
-
0.2
5
"A
V
1.25
1.30
-
0.02
0.05
-
20
0,3
-
1.20
125
1,30
-
0.02
0.07
50
1
-
20
0,3
70
1.5
mV
%VO
0.7
-
-
0.7
-
%VO
-
3.5
5
--
3.5
10
0.5
0.15
0.9
0.25
-
0.5
0,15
0.9
0,25
-
-
0,003
-
-
0.003
-
-
-
-
66
65
80
66
65
80
-
-
0,3
1
-
0.3
-
7
7
-
-
-
7
7
%/V
Regload
mA
A
'max
N
%VO
RR
Cad,=10"F
Long Term Stability, TJ = Thigh INote 6)
TA:: 25°C for Endpoint Measurements
Min
%/V
1.20
VI-Va';; 15 V, PD';; Pmax
VI-Va = 40 V, PO';; Pmax , TA = 25°C
NOTES
(1) Tlow=-55°CforLM117M
:: -25°C for LM217M
Ooefor LM317M
LM117M/217M
Min
Typ
Max
dB
S
1
%/1.0 k
Hrs.
°C/W
ROJC
Thigh = +150°C for LM117M
=+150°C for LM217M
= +125°C for LM317M
-
(4) Selected devices with tightened tolerance reference voltage available.
(5) CadJ' when used, IS connected between the adjustment pin and ground
=7,5 W
(6) Since Long Term Stability cannot be measured on each device before
shipment, this specification IS an engineering estimate of average
stability from lot to lot
(3) Loadand Ime regulation are specified atconstantJunctiontemperature.
Changes in Va due to heating effects must be taken lOto account
separately. Pulse testing with low duty cycle is used.
184
LM117M, LM217M, LM317M
SCHEMATIC DIAGRAM
Vino---~------'--------'--------~-------------1r--'--------~-----'---1r-----'---,
6.8 V
6av
350
1.25
2 k
6 k
L....-4'"-''W'Ir-....."'VV'v-----o Ad] ust
FIGURE 1 - LINE REGULATION AND
~IAdj/LINE
TEST CIRCUIT
Vcc
Lme Regulation (O/O/V) =
V out
LM117M
Adjult
R
1
• Pulse Testing Required:
1% DutY Cyel.
II luggested.
185
.> 240
1%
VOH-VOL
VOL
X 100
LM117M, LM217M, LM317M
FIGURE 2 - LOAO REGULATION ANO 41Adj/LOAD TEST CIRCUIT
Loec:t A ..... I.tlon (mV) ~ Vo (min. Lo.d) - Vo (m.x. Loec:t)
Vo (min. Lo.d) - Vo (m.x. Load)
--, rVO ( I L d)
Vo (min. Load)
X 100
U V
m n. o.
'
Vo (max. Lo.d)
Lo.d Aegul.tlon ("VO) ~
Vout
LMI17M
240
Adjust
AL
(min. Load)
1"
O.I1'F
• Pul .. Testing Required:
1" Duty Cyel. II sug....tec:t.
FIGURE 3 - STANDARD TEST CIRCUIT
V out
LMI17M
240
1%
Vo
To Calculate R 2·
Vo = ISET A2 + 1.250 V
Assume ISET ::::: 5.25 mA
Pul .. Taltln" Required:
1" Duty Cvel. Is lugge.ted.
FIGURE 4 - RIPPLE REJECTION TEST CIRCUIT
24V - "
.
14V---V
V out
Vln
Vo
~ ~O
LMI17M
I-120Hz
Al <
Cln
:;:r:
°1"
240
Adjust
1"
..
~ lN4002
~
...L+
Co ........ I1'F
0.1 I'F
..
1.65 k
R2
_L..
1+
~
Cadj ;7:: 10l'F
1"
1
1
.
01 Discharges Cadjlf Output IS Shorted to G r ound
• ·Cedj provide. an AC Ground to the Adjust Pin.
186
RL
Vo
v
LM117M, LM217M, LM317M
FIGURE 5 - LOAD REGULATION
FIGURE 6 - RIPPLE REJECTION
90
~
0.4
I
w
~
«
O. 2
~
/
w
to
«
!:i
o
~
"
~
>~ -0. 6
70
w
~
~
o
~F
/
60 f- IL = 100mA
f = 120 Hz
~ -0. 8
Without Cadj
- r--
~
~
~
~.
Withl Cadi = 10
r-- -L
E
VI = 10 V
Vo = 5 V
'L = 5 to 500 rnA
~ -0. 4
80
z
0
" ---J-:
-0. 2
>
-
I
VI = 45 V
Vo = 5 V
IL = 5to40mA
/
f..-i
f- VO=10V
VI= 14t024V
-1. 0
50
- 50
- 25
25
50
75
100
TJ, JUNCTION TEMPERATURE 1°C)
125
150
- 50
FIGURE 7 - CURRENT LIMIT
~ 0.80
-""" ""
>-
~
'":::>
0.60
"
(.)
>-
~
:::>
o
r:::::::: r - t-- t-i'.
TJ = 1500
o
IL=100mA
10
30
40
20
VI- VO, INPUT - OUTPUT VOLTAGE OIFFERENTIAL (VOLTS)
-50
_
TJI=550cl__ ~
>- 3.5 -
TJ=250C--TJ=1500C---
~:;
d
2.5
2.0
1.0
0,5
50
25
75
100
125
150
TJ, JUNCTION TEMPERATURE 1°C)
FIGURE 10 - RIPPLE REJECTION versus FREQUENCY
90
~
3.0
1.5
-25
100
4.5
a'">-
-
0.5
50
FIGURE 9 - MINIMUM OPERATING CURRENT
~
r-- r--
~
5.0
4.0
150
""- b-,.
- 0.20
«
.§
IL = 500 mA
r--- r--
TJ = 250C
'" 0'" ""-
0.40
o
o
125
2.5
f---
!!
25
50
75
100
TJ, JUNCTION TEMPERATURE 1°C)
FIGURE 8 - DROPOUT VOL TAGE
1.0
[
- 25
,- ~ ~.....
V'"
n ...
~
z
o
/"
~
~
0/
I
i--
\
0
0
w
~ 40
a:
1"'-
\
\
\
30
0
10
10
20
30
40
10
V,- Vo, INPUT - OUTPUT VOLTAGE DIFFERENTIAL (VOLTS)
187
100
lK
I
IL=40mA
_
VI'" 5 V ± 1 Vpp
Vo = 1.25V
......
8
70
10K
100 K
1m
I, FREQUENCY (Hz)
LM117M, LM217M, LM317M
FIGURE 11 - TEMPERATURE STABILITY
FIGURE 12 - ADJUSTMENT PIN CURRENT
1.260
<
.3
:>
;:;; 1.250
'";
o
/'
/
>
w
~ 1.240
:--. ...........
:! 1.230 r--0:
_
-
_
....
ill
65
....
60
0:
0:
::>
f"-.. I'-....
.1
0:
....
....
z
55
:IE
50
In
=l
0
V,·4.2V
VO'Vref
'L • 5 mA
<
45
:is'
$- 40
1.220
,,/
r--- -
w
-25
25
50
15
100
TJ, JUNCTION TEMPERATURE (DC)
125
150
-50
0.2 f----- -
I
-25
25
50
15
100
TJ, JUNCTION TEMPERATURE (DC)
125
150
---0.2
>
f--
-O.S
/
Bandwidth 100 Hz to 10 kHz
~ -0.4
....
g
---
0:::
II
w
'"
~
-
FIGURE 14 - OUTPUT NOISE
V,' 4.25 to 41.25 V
VO'Vrel
'L '50mA
5
o
L.-:::
r
FIGURE 13 - LINE REGULATION
~
<
~
k::"'-
35
-50
0.4
1
w
;
~
.!
V,-6.25V
VO'V"f
---IL '10mA
--IL'100mA
z
1/
~
10 ' - -
6
::; -O.B
---
.,-
~
w
-
10
'"<
~ 80
o
>
V
w
!!2
o
'"
-1.0
--
./
--
'/
V
V
V
6.0
4.0
-50
-25
25
50
15
100
TJ,JUNCTION TEMPERATURE (DC)
125
150
-50
FIGURE 15 - LINE TRANSIENT RESPONSE
-25
25
50
15
100
TJ, JUNCTION TEMPERATURE (DC)
125
150
FIGURE 16 - LOAD TRANSIENT RESPONSE
,.."
,
5
0
5
0
w
'"<~>
0-
>w
o. 5
:!!:5
~
0
I _
Vo '1.25 V
'L·20mA
TJ' 250 C
'I
A
2
L
3
I
I" C \• 0
I
"
20
t, TIME
30
,,
'I
:1
I\Ut "\1
I
I
~
V, • 15 V
CL ·0.3pF;C,dj·'OpF -VO.,OV
~L'10mA
J.25 0 C
.I
40
10
188
-
-
~"""'IL
\ I
V
(.~
,,
I
0;>
-J
10
1
I.
1
_,
CL'1 ~F;C.dj·'O~
-j
J.
O~
~~
... <
,'\..
-1. 5
1.
2
CL ' I.F
f\
20
t,TIME
30
("~
40
LM117M, LM217M, LM317M
APPLICATIONS INFORMATION
BASIC CIRCUIT OPERATION
EXTERNAL CAPACITORS
The LM 117M is a 3-terminal floating regulator. In
operation, the LMl17M develops and maintains a nominal
1.25 volt reference (Vref) between its output and adjustment terminals. This reference voltage is converted to a
programming current (lprog) by Rl (see Figure 17),
and this constant current flows through R2 to ground.
The regulated output voltage is given by:
A 0.1 p.F disc orl p.F tantalum input bypass capacitor
(Cin) is recommended to reduce the sensitivity to input
line impedance.
The adjustment terminal may be bypassed to ground to
improve ripple rejectIOn. This capacitor (Cadj) prevents
ripple from being amplified as the output voltage is
increased. A 10 p.F capacitor should improve ripple
rejection about 15 dB at 120 Hz in a 10 volt application.
Although the LM 117M is stable with no output capacitance, like any feedback circuit. certain values of external
capacitance can cause excessive ringing. An output
capacitance (Co) in the form of a 1 p.F tantalum or 25 p.F
aluminum electrolytic capacitor on the output swamps
this effect and insures stability.
R2
Va = Vref (1 + R1) + ladjR2
Since the current from the adjustment terminal (ladj)
represents an error term in the equation, the LM 117M
was designed to controlladj to less than 100 p.A and keep
it constant. To do this, all quiescent operating current is
returned to the output terminal. This imposes the requirement for a minimum load current. If the load current IS
less than this minimum, the output voltage will rise.
Since the LM117M is a floating regulator, it is only the
voltage differential across the circuit that is important
to performance, and operation at high voltages with
respect to ground is possible.
PROTECTION DIODES
When external capacitors are used with any I.C. regulator It is sometimes necessary to add protection diodes to
prevent the capacitors from discharging through low
current points into the regulator.
Figure 18 shows the LM 117M with the recommended
protection diodes for output voltages in excess of- 25 V or
high capacitance values (Co> 10 p.F, Cadj > 5 p.F).
Diode 01 prevents Co from discharging thru the I C.
during an input short circuit. Diode 02 protects against
capacitor Cadj discharging through the I.C. during an
output short cirCUIt. The combination of diodes 01 and
D2 prevents Cadj from discharging through the I.C. during
an Input short CirCUit.
FIGURE 17 - BASIC CIRCUIT CONFIGURATION
Vin
LM117M
l
I
v out
!
\
vref
Adjust
--
+
R1
l'p'09
= 1.25 V
FIGURE 18 - VOLTAGE REGULATOR WITH
PROTECTION DIODES
Vo
ladj
V,ot
r
R2
TYPICAL
1
°1
IN4002
-:::-
LOAD REGULATION
The LMl17M is capable of providing extremely good
load regulation, but a few precautions are needed to
obtain maximum performance. For best performance, the
programming resistor (Rl) should be connected as close
to the regulator as possible to minimize line drops which
effectively appear in series with the reference, thereby
degrading regulation. The ground end of R2 can be
returned near the load ground to provide remote ground
sensing and improve load regulation.
189
LM117M, LM217M, LM317M
FIGURE 19 - ADJUSTABLE CURRENT LIMITER
FIGURE 20 - 5 V ELECTRONIC SHUTDOWN REGULATOR
2.5 k
V out
A2
500
01
I N914
L -_ _ _ _ _ _ _ _ - - - - - .
-To provide current limiting of 10 to
the system ground, the source of the
current limiting diode must be tied
02
lN914
Adjust
to a negative voltage below -7.25 V.
A
2
Al
,~
{.IF
0-----<.....---'
.r-
MPS2-222
TTL
720
Control
I k
I N5314
lOSS
~
11.0
120
Vref
lOmax + lOSS
Va < POV + 1.25 V + VSS
I Lmin ~ Ip
'0 < 500 rnA As shown 0
'0 < 495 rnA
<
<
Minimum
Ip
Va
=
1.25 V
01 protects the deVice dunng an Input shott ClrCUI!
FIGURE 22 - CURRENT REGULATOR
FIGURE 21 - SLOW TURN-ON REGULATOR
V aut
IN4001
Adjust
Q - - - - -...
lOmax
V,e! )
( ~
+ ladj
,,~
Al
_ 1.;25 V
V,e!
)
+ ladj
~ A I + A2
Rl + R2
IOrnin = ( - - - - -
5 rnA
190
<
'out
<
500 rnA
®
LM123, LM123A
LM223, LM223A
LM323, LM323A
MOTOROLA
Specifications and Applications
InforIllation
3-AMPERE. 5 VOLT
POSITIVE
VOLTAGE REGULATOR
SILICON MONOLITHIC
INTEGRATED CIRCUIT
3 AMPERE. 5 VOLT POSITIVE VOLTAGE REGULATOR
The LM123. A/LM223. A/LM323. A are a family of monolithic integrated C"CUltS which supply a fixed positive 5.0 volt output with a
load driving capability In excess of 3.0 amperes. These threeterminal regulators employ Internal current limiting, thermal
shutdown, and safe-area compensation. An Improved series with
superior electrical characteristics a nd a 2% output voltage tolerance
IS available as A-suffIX (LM123A/LM223A/LM323AI device types.
These regulators are offered in a hermetic TO-3 metal power
package In three operating temperature ranges. A O°C to +125°C
temperature range version is also available in a low cost TO-220
plastic power package.
Although deSigned primarily as a fixed voltage regulator, these
deVices can be used with external components to obtain adjustable
voltages and currents. This series of deVices can be used with a
series pass transistor to supply up to 15 amperes at 5.0 volts.
•
Output Current
•
Available with 2% Output Voltage Tolerance
In
K SUFFIX
METAL PACKAGE
CASE 1
(TO-3 Type)
Pm 1
2
CASE
(Bottom View)
Excess of 3.0 Amperes
•
No external Components Requ"ed
•
Internal Thermal Overload Protection
T SUFFIX
PLASTIC PACKAGE
(LM323 and LM323A)
•
Internal Short-Circuit Current Limiting
•
Output TranSistor Safe-Area Compensation
•
Thermal Regulation and Ripple Rejection Have Specified Limits
CASE 221A
(TO-220)
Pin 1
2.
3
MAXIMUM RATINGS
Value
Unit
Vdc
Input Voltage
Vm
20
Power DISSipation
PD
Internally Limited
TJ
-55 to +t 50
-25 to +150
Oto+125
°C
Tsto
-65 to +150
°C
T solder
300
°C
Operating Junction Temperature
Range
Storage Temperature Range
Lead Temperature (Soldering, las)
LMt23, A
LM223, A
LM323, A
(Heatslnk surface connected
STANDARD APPLICATION
In pu t $ M 1 2 3 , A Output
ORDERING INFORMATION
Output Voltage
1
INPUT
2
GROUND
OUTPUT
to Pm 2)
Symbol
Rating
Tolerance
Junction
Temperature Range
LM123K
LM123AK
6%
-55 to +150 oC
LM223K
LM223AK
6%
2%
-25 to +150°C
LM323K
LM323AK
4%
o to +125°C
LM323T
LM323AT
4%
2%
Device
INPUT
OUTPUT
GROUND
Package
Metal Power
2%
Cin'
0.33 pF
CO"
A common ground IS required between the
input and the output voltages. The input voltage must remam tYPically 2.5 V above the output voltage even dunng the low point on the
input ripple voltage
* ;: : Cin IS reqUired if regulator IS located an
appreciable distance from power supply
filter. (See Applications Information for
details.)
2%
Plastic Power
191
** = Co
is not needed for stability; however,
it does improve transient response.
LM123, LM123A, LM223, LM223A, LM323, LM323A
ELECTRICAL CHARACTERISTICS (TJ: Tlow to Thigh [see Note
Characteristic
Symbol
LM123/LM223
Typ
Max
Min
Min
LM323
Typ
Max
Unit
Vo
4.9
5.0
5.1
47
5.0
5.3
4.8
5.0
52
V
Vo
4.8
50
52
4.6
5.0
54
475
5.0
525
V
Regime
-
1.0
15
-
10
25
-
10
25
mV
Reg'oad
-
10
50
-
10
100
-
10
100
mV
Regtherm
-
0.001
001
-
0002
003
-
0002
0.03
%VO/W
Ie
-
35
10
-
35
20
-
35
20
mA
VN
-
40
-
-
40
-
-
40
-
~Vrms
RR
66
75
-
62
75
-
62
75
-
de
-
4.5
55
-
-
45
5.5
-
-
45
55
-
5
-
-
35
-
-
35
-
-
35
mV
ROJC
-
20
-
-
20
-
-
2.0
-
°C/W
Output Voltage
(VIn:
lJ unless otherwise specified)
LM 123A/LM223AI LM323A
Max
Min
Typ
7 5 V, 0,,;; lout";; 3.0 A, TJ : 25°C)
Output Voltage
(75 V";; V,n";; 15 V,O";; lout";; 3.0 A,
P ~ Pmax [Note 2])
Lme Regulation
(75 V,,;; VIn
";;
15 V, TJ: 25°C) (Note 3)
Load Regulation
(V in : 7.5 V, 0";; lout";; 3.0 A, TJ : 25°C)
(Note 3)
Thermal Regulation
(Pulse: 10 ms, p: 20 W, TA: 25°C)
QUiescent Current
(75 V,,;; VIn
";;
15 V, 0";; lout";; 3 0 A)
Output NOise Voltage
(10 Hz";; f";; 100 kHz, TJ: 25°C)
Ripple Rejection
(B.O V::;;; Vin ::;;; 18 V, 'out::: 2 0 A.
f: 120 Hz, TJ: 25°C)
Short CirCUIt Current Limit
(VIn:
(VIn
:
ISC
15V, TJ:25°C)
7 5 V, TJ: 25°C)
Long Term Stability
Thermal ReSistance Junction to Case
A
-
(Note 4)
Note 1 Trow = -55°C for LM123, A
Thigh::: +150oC for LM123, A
: -25°C for LM223. A
O°C for LM323, A
: +150o C for LM223, A
: +125°C for LM323, A
Note 3 Load and line regulation are specified at constant Junction tern·
perature Pulse testing IS required With a pulse Width ~ 1 0 msand
a duty cycle ~ 5%.
Note4. Without a heat Sink, the thermal resistance (R 6JA) Is35°C/Wfor
the TO·3, and 65°C/Wforthe TO·220 packages With a heat Sink,
the effective thermal resistance can approach the specified values
of 2 0 °C/W, depending on the effiCiency of the heat Sink.
Note 2. Although power diSSipation IS rnternally limited, specificatIOns
apply only for P ~ Pmax
Pma . : 30 W for K (TO-3) package
Pmax = 25 W for T (TO-220) package
VOLTAGE REGULATOR PERFORMANCE
The performance of a voltage regulator is specified by Its Immunity to changes In load, Input voltage, power dissipation, and
temperature. Line and load regulation are tested with a pulse of
short duration « 100 I'S~ and are strictly a function of electrical
gain. However, pulse widths of longer duration (> 1.0 ms) are
sufficient to affect temperature gradients across the die. These
temperature gradients can cause a change in the output voltage,
in addition to changes caused by line and load regulation. Longer
pulse widths and thermal gradients make It desirable to specify
thermal regulation.
Thermal regulation IS defined as the change in output voltage
caused by a change in diSSipated power for a specified time, and
is expressed as a percentage output voltage change per watt. The
change in diSSipated power can be caused by a change In either
the input voltage or the load current. Thermal reg ulatlon IS a function of I.e. layout and die attach techniques, and usually occurs
within lams of a change In power dissipatIOn. After lams, additional changes In the output voltage are due to the temperature
coefficient of the device.
Figure 1 shows the line and thermal regulation response of a
typical LM 123A to a 20 watt Input pulse. The variation of the output voltage due to line regulation is labeled
and the thermal
regulation component is labeled
Figure 2 shows the load and
thermal regulation response of a typical LM 123A to a 20 watt load
pulse. The output voltage variation due to load regulatIOn is labeled
and the thermal regulation component IS labeled
0.
CD
192
CD
0.
LM123, LM123A, LM223, LM223A, LM323, LM323A
SCHEMATIC DIAGRAM
Input
OZ6
3 Ok
03
10pF
10k
300
OZ3
13
012
zoo
50
Output
840
72 k
06
56V
17k
Gnd
FIGURE 1 -
:;;-
LINE AND THERMAL REGULATION
FIGURE 2 - LOAD AND THERMAL REGULATION
18 V
~
:::,w
0..<0
~-
:::."
z ..
-.!:i
>5~ B.O V
0..~~
:::.Z
OW
.d~
~:::.
-S>u
t. TIME 12.0 ms/div.1
t TIME (2.0 ms/div·1
LM123A
Vo = 5.0 V
Vin = 15
lout = 0 A_2.0 A-O A
LM123A
Vo = 5.0 V
Vin = 8.0 V -18 V-8.0 V
/
o
?
490
-90
-50
-10
30
70
110
150
10-3
10-4
10
10
190
100
10k
TJ. JUNCTION TEMPERATURE (OC)
i
0
0..
0..
I
I--- f- Yin = 10 V
~ 40
~ f-
~
0;
~
z
\
Co = 0
TJ = 25°C
20
10
10
~
0:
~
0..
0..
\
100
10k
10k
60 1---
0;
r---
or'
0:
1\
\
I
lOOk
40
10M
10M
30
0.01
100M
I. FREOUENCY (Hz)
0
0
0
JJ
TJ = 150°C
-\
j
\ IJ-.
U
01
1.0
10
5.0
TJ 1=
TJ = 25°C
«
1TJ = 25°e
!i;
~ 3.0
~ = 150JC
..,=>
!i5 2. 0
..,
'out = 2.0 A- ~
:.L1...1
I
~
g
TJ = -we
~l TJl250e I
o\;
I
~55JC
j
4. 0
~
i' TJ = 150°C
"
5.0
11m
FIGURE 8 - QUIESCENT CURRENT versus
OUTPUT CURRENT
I
TJ = -55°C
/I
Vin= 10V
Co = 0
1= 120 Hz
TJ = 25°C
'out. OUTPUT CURRENT (A)
FIGURE 7 - QUIESCENT CURRENT versus
INPUT VOLTAGE
40
100M
-
80
o
~
lout = 30 A
10M
r----
~
/
z
o
10M
100
t
;;-
I----
lOOk
FIGURE 6 - RIPPLE REJECTION versus
OUTPUT CURRENT
'out = 50 rnA
~ 80
10k
I. FREOUENCY (Hz)
FIGURE 5 - RIPPLE REJECTION versus FREQUENCY
100
J
Vi~ =1 10 ~
.rP 1.0
I I I
10
15
0
0.01
20
Vin. INPUT VOLTAGE (Vdc)
I
0.1
1.0
'out. OUTPUT CURRENT (A)
194
10
LM123, LM123A, LM223, LM223A, LM323, LM323A
FIGURE 10 - SHORT CIRCUIT CURRENT
FIGURE 9 - DROPOUT VOLTAGE
2.5
I--
B0
I ,In
-
lout = 3 0 A
--- - -
r::-
""-
r--
lout = IDA
.......::..L ~
~-
---J-=r:-
I-
I~ut ='0 5 A - I--
6Vo = 50 rnV
0.5
-90
o
-50
-10
70
30
110
50
190
150
FIGURE 12 -
I
,I
lout = 150 rnA _
Co = 0
TJ = 25°C
4
3
r-
'"
r---
o'='
>
2
VI~ = 10 'V
1
Co = 0
TJ = 25°C
0
5~
~ ~-O
of::
I
~~-o 2
2
<10
4
5
?
?
0
0
5
5
0
0
f::
\
\
40
FIGURE 14 - MAXIMUM AVERAGE POWER
DISSIPATION FOR LM323K
~
40
z
OSA of Heat Sinks
0SA of Heat Sinks
0
f::
MaXimum Amblent_+-_-I
;;:
u;
~
U>
Q
Q
co
co
~
~
>
---o-:; 10k
1 k
The LM123, A regulator can also be used as a current source when connected as above ReSistor R determines the current as follows
5V
10 =
610
== 0.7
R
+ IQ
Vo. 8.0 V 10 20 V
V in - Vo ~ 2 5 V
mA over line, load and temperature changes
'0'" 3.5 mA
The addition of an operational amplifier allows adjustment to higher or
Intermediate values while retaining regulation characteristics The mini-
For example, a 2-ampere current source would require R to be a 2.5 ohm,
15 W resistor and the output voltage compliance would be the Input voltage less 7 5 volts
mum voltage obtainable With thiS arrangement IS 3 0 volts greater than
the regulator voltage
FIGURE 18 - CURRENT 800ST WITH
SHORT·CIRCUIT PROTECTION
FIGURE 17 - CURRENT BOOST REGULATOR
2N4398
2N4398 or Equlv
'"."'~ ,M'''A ~o,"",
1.0l'F:J
1
or Equlv
Input
R
:J011'F
The LM 123, A series can be current boosted with a PNP transistor. The
The circuit of Fig ure 17 ca n be modified to provide supply protection against
short CirCUIts by adding a short-circuit sense resistor, RSC' and an additional PNPtransistor. The current sensing PNP must be able to handle the
short-cIrcuit current of the three-terminal regulator. Therefore, an eightampere plastic power transistor is specified.
2N4398 provides current to 15 amperes. Resistor R In conjunction with
the VBE of the PNP determines when the pass transistor beginS conducting; thiS CIfCUlt IS not short-circuit proof. Input-output differential voltage
minimum is Increased by the VBE of the pass tranSistor.
196
®
LM137
LM237
LM337
MOTOROLA
Specifications and Applications Information
3-TERMINAL ADJUSTABLE
OUTPUT NEGATIVE VOLTAGE REGULATOR
The LM 137/237/337 are adJustabJe 3-terminal negative voltage
regulators capable of supplying In excess of 1.5 A over an output
voltage range of -1.2 V to -37 V These voltage regulators are
exceptionally easy to use and require only two external resistors to
set the output voltage. Further, they employ internal current
limiting, thermal shutdown and safe area compensation, making
them essentially blow-out proof.
The LM137 series serve a wide variety of applications Including
local, on-card regulation. This device can also be used to make a
programmable output regulator; Of, by connecting a fixed resistor
between the adjustment and output, the LM137 series can be used
as a precision current regulator.
3-TERMINAL
ADJUSTABLE NEGATIVE
VOLTAGE REGULATOR
SILICON MONOLITHIC
INTEGRATED CIRCUIT
K SUFFIX
METAL PACKAGE
CASE 1
(TO-3 Type)
(Bottom View)
Case
•
Output Current In Excess of 1.5 Ampere In TO-3 and TO-220
Packages
•
Output Current in Excess of 0.5 Ampere In TO-39 Package
•
Output Adjustable Between -1.2 V and -37 V
•
Internal Thermal Overload Protection
•
Internal Short-Clrcult-Current Limiting, Constant with
Temperature
•
Output Transistor Safe-Area Compensation
•
Floating Operation for High Voltage Applications
•
Standard 3-Lead Transistor Packages
•
Eliminates Stocking Many Fixed Voltages
IS
Input
Pins 1 and 2 electrically iSOlated from case.
Case is third electrical connection.
T SUFFIX
PLASTIC PACKAGE
(LM337 only)
CASE 221A
(TO-220)
Pin 1
Adjust
PH,2
V in
Pin 3
V out
Heatsink surface connected
to Pin 2
STANDARD APPLICATION
H SUFFIX
METAL PACKAGE
CASE 79
R2
(TO 39)
R1
120
ladj
". . . ."!Jj
C ••
o
Adjust
(Bottom View)
Pin 1
Adjust
Pin 2 Output
Pin 3
Input
ORDERING INFORMATION
Civic.
·ein is required if regulator is located more than 4 inches from power supply
filter. A 1 ~F solid tantelum or 10 ~F aluminum electrolytic is recommended.
BC Ois necessary for stability, A 1 ,uF solid tantalum or 10,uF aluminum electrolytic is recommended,
197
LM137H
LM137K
LM237H
LM237K
LM337H
LM337K
LM337T
Temperature Ringe
Plcklge
to +1 SOoC
to +160 Cl C
to +1 SOoC
to t-1 60@C
TJ"" O@Clo+12S e C
TJ" Q"C to +126"C
TJ ~ OtlC 10 +126°C
Metal Can
Metal Power
Metal Can
Metal Power
Metal Can
Metal Power
Pioslie Power
TJ < ~56(JC
TJ' ~56°C
TJ' ~26°C
TJ" -26°C
LM137, LM237, LM337
MAXIMUM RATINGS
Rating
Input-Output Voltage Oifferentlal
Symbol
Value
Unit
VI-Va
40
Vdc
Po
Internally Limited
TJ
-55 to +150
-25 to +150
Oto+125
°C
Tstg
-65 to +150
°C
Power DisSipation
Operatmg JunctlOn Temperature Range
LM137
LM237
LM337
Storage Temperature Range
ELECTRICAL CHARACTERISTICS
(IVI- Vol = 5 V, 10=0.5Afor KandTpackages, 10=0.1 Alar Hpackage, TJ= TlowtoThlghlsee
r~ote 1].
Characteristic
Line Regulation (Note 3)
TA =25°C, 3 V';; lVI-Vol,;;; 40 V
Load Regulation (Note 3),
TA =26°C, 10 mA ';;'10';;; I max
IVai ,;;;5V
IVol;.SV
Thermal Regulation
10 mS Pulse, TA =25°C
Adj~stment
Pin Current
Adjustment Pin Current Change
2.5 V,;; lVI-Vol,;; 40 V,
10 mA,;; IL ';;-I max,
PO';; Pmax , TA = 25°C
Relerence Voltage (Note 4)
3 V';; lVI-Vol,;;; 40 V, 10 mA'';' 10";; I max ,
PO';; Pmax , TA =25°C
Tlow to Thigh
Line Regulation (Note 3)
3 V';;; lVI-Vol ,,;;40V
Load Regulation (Note 3)
10 mA,;; 10';;; Imax
IVai,;;; 5V
IVai;. 5 V
Temperature Stability (Tlow";; TJ";; Thiah)
Minimum Load Current to
Maintain Regulation (lVI-Vol,;;; 10 V)
(lVI-Vol,;;; 40 V)
Maximum Output Current
lVI-Vol,;; 15 V, PO';;; Pmax
K and T Packages
H Package
lVI-Vol ,;; 40 V, Po';;; Pmax , TJ = 25°C
K and T Packages
H Package
Imax and Pmax per Note 2. unless otherwise specIfied)
Figure
Symbol
1
Regline
2
Regload
Min
-
LM137/237
Typ
Max
-
0.01
0.04
Unit
%/V
-
15
0.3
250.5
-
-
15
0.3
50
1.0
mV
%VO
0.003
0.04
%VO/W
65
100
"A
2.0
5.0
"A
-
0.002
0.02
3
1,2
ladj
-
65
2.0
100
"'dadj
3
Vrel
2
Regload
3
TS
3
ILmin
5.0
-
-
V
-1.225
-1.20
-
-1.250
-1.25
-1.275
-1.30
0.02
0.05
-
20
0.3
-
0.6
50
1.0
-
-
1.2
2.5
3.0
5.0
3
Max
0.02
Regtherm
Reglin",
LM337
Typ
0.01
-
1
Min
-1.213
-1.20
-
-1.250
-1.25
-1287
-1.30
0.02
0.07
%/V
-
20
0.3
mV
%VO
-
0.6
70
1.5
-
-
1.5
2.5
6.0
10
-
I max
RMS Noise, % 01 Va
TA =25°C, 10Hz';; I';; 10kHz
-
N
Ripple Rejection, Va =-10 V, I - 120 Hz
(Note 5)
Without Ca~
Cad' =10"
Long Term Stability, TJ =Thigh (Note 6)
TA = 25°C Iqr Endpoint Measurements
Thermal Resistance Junction to Case
H Package (TO-39)
K Package (TO-3)
T Package (TO-220)
4
RR
A
1.5
0.5
2.2
0.8
-
0.24
0.15
0.4
0.20
-
0.003
S
-
R6JC
1.5
0.5
2.2
0.8
-
0.15
0.10
0.4
0.20
-
-
0.003
~
-
-
-
%VO
dB
3
%VO
mA
-
-
-
NOTES.
(1) Tlow
=-55°C for LM137
Thigh =+15QoC for lM137
::: -25°C for LM237
::: +150°C for LM237
OOC for LM337
= +125°C for LM337
(21 Imax = 1 5 A for K (TO-3) and T (TO-220 Packages
= 0.5 A for H (TO-39) Package
Pmax = 20 W for K (TO-31 and T (TO-2201 Packages
= 2 W for H (TO-39) Package
(3) Load and line regulation are speCified at a constant Junction temperature. Pulse testing With a low duty cycle IS used Change in Va because
of heating effects IS covered under the Thermal Regulation specification.
(4) Selected devices with tightened tolerance reference voltage available.
-
-
-
77
0.3
1.0
66
-
12
2.3
15
3.0
-
60
66
-
60
77
-
-
0.3
1.0
12
2.3
4.0
15
3.0
%/l.0k
Hrs.
°C/W
-
-
-
-
(5) CadJ- when used, IS connected between the adjustment pin and
ground
(6) Since Long Term StabIlity cannot be measured on each devIce before
shipment, thiS speCIfication IS an engineering estimate of average
stability from lot to lot.
(7) Power dissipation Within an I C. voltage regulator produces a temperature gradient on the die. affect 109 Individual I C components on the die.
These effects can be minimized by proper Integrated CirCUit design and
layout techniques. Thermal Regulation IS the effect of these temperature gradients on the output voltage and IS expressed 10 percentage of
output change per wan of power change in a specified time
198
LM137, LM237, LM337
SCHEMATIC DIAGRAM
60
--
loot
~
25k~
X"
810
~
Adlust
2k
L-+--
r1
0
0
10 k
r'
u.
f
j¥
60k
I~
~
.-1
15 pF
100k
18 k
0
0
ro
~
,)
"'
N
h..
2k
I
f/
~
"-
"~
f#
5k
L.....t 750
~
H:
4k
f/
ho..
" -Q
6k
K
~
ho..
100
~~
)-~~ H:i:
Y:
~
100 pF ,
0
N
100k
~
en
4k
500
N
24 k
30 k
>--"Nv-
240
01:
2 pF
,n
N
~
~
50k
.,.
600
r
h..
18 k
5 pF
~
8k
220
ro
u.
500
15
o. 2
15
155
O. 05
FIGURE 1 - LINE REGULATION AND -'lodi/LiNE TEST CIRCUIT
R2
1%
1.0 "F
1 I'F
R1
* Pulse Testing Required:
1 % Duty Cycle
is suggested.
V out
120
1%
-, r-
u ____
199
VOH
VOL
LM137, LM237, LM337
FIGURE 2 - LOAD REGULATION AND :'Iad/LOAD TEST CIRCUIT
R2
1%
* Pulse Testing requ Ired:
1% Duty Cycle is suggested.
..JL
RL
(max.
Load)
-Va (min. Load)
Va
Load Regulation (mV) = Va (min. Load) -
Va (max. Load)
Load Regulation (%V o
)
Va
=
(max. Load)
(min. Load) - Va (max. Load)
Va (min. LO~d)
FIGURE 3 - STANDARD TEST CIRCUIT
R2
1%
Va
120
To Calculate R2:
R2=(~-1)Rl
Vref
Pulse Testing Required.
This assumes lad)
IS
negligible.
1 % Duty Cycle is suggested.
FIGURE 4 - RIPPLE REJECTION TEST CIRCUIT
i
J,
-1...+
R2
Cin
Cad] 1'10J..LF
1%
I
r- 10 I'F
Adjust
R1
Vin
+
CO
I
I
LM137
I
01'
120
A~
1
I'F
Va
RL
1N4002
V out
I
va
~
1.25
14.3V ____~
4.3 V - ___' ___ ~
*01 Discharges Cadi jf Output is shorted to Ground.
f=120Hz
200
v
100
LM137, LM237, LM337
FIGURE 6 - CURRENT LIMIT
FIGURE 5 - LOAD REGULATION
0.2
---
~
- --
w
to
-0.2
~
-0.4
z
w
to
"'"
-0.6
0
>
~
-0.8
'"6
-1.0
f0
>
~
VI
~
.. _.-
"'""'-\
~
~
~
i:5
e-
'"
r-
~
~
IL
-15 V
!;
1.5 A
o
_0
1
I
o
-1.4
-50
-25
0
25
50
75
100
125
TJ, JUNCTION TEMPERATU RE (oC)
150
T
o
~
- -- -
75
~
'"z
70
~
65
u
0:
i'-- r--
~
60
f-
"-'"
H- Packaged DeVices
- ---
'....
-
~"
~~ 0-::--
- ----~--- -- - -
10
20
30
VI - V O' INPUT - OUTPUT VOLTAGE DIFFERENTIAL (Vdcl
FIGURE 8 - DROPOUT VOL TAGE
~
f-
~
I.l
FIGURE 7 - ADJUSTMENT PIN CURRENT
80
;;'
3
~ -5~OC
TJ ~ 25 0 C
TJ ~ 150 0 C
T- and K- Packaged Dev!ces
§
I---
TJ
--
0.5 A
~
VO~·10V
-1.2
Z
:;:
§
'"-c
::-
~
55
!;
0
50
I
~
--
45
'"
40
·50
·25
1.5
25
50
75
100
TJ,JUNCTION TEMPERATURE (oC)
125
150
·50
-25
50
75
100
25
TJ, JUNCTION TEMPERATURE (oC)
-
1.8
;;'
~1.26U
5
w
;o
-
~ 1.250
~
r--.
g
§
~
~
1.2
'"u
1.0
'"d
f-- f-
-50
-25
25
50
75
100
125
TJ,JUNCTION TEMPERATURE (oC)
.
."/
V
0.6
o
150
~
of/'
TJ ~ 150 0 C
~
0.8
0.2
I-55 a C
~
)"-
F- --
d> 0.4
"
>
T
,............ I-- TJJ ~ 25 0 C
1.6
1.4
g
~ 1.240
1.230
150
FIGURE 10 - MINIMUM OPERATING CURRENT
FIGURE 9 - TEMPERATURE STABILITY
1.270
to
125
----: I;?'
I
o
10
20
30
40
VI - VO' INPUT - OUTPUT VOLTAGE DIFFERENTIAL (Vdcl
201
40
lM137, lM237, lM337
FIGURE 11 - RIPPLE REJECTION VS OUTPUT VOL TAGE
FIGURE 12 - RIPPLE REJECTION VS. OUTPUT CURRENT
100
100
Cadi'" 10 pF
~
;'5
i3
40
VI -Vs=5V
IL "50 mA
I" 120 Hz
TJ "250C
-
~-
20
o0
-10
-5
I,
i
W,thoul Cadi
u
w
w
60
~
w
I
~
~
~
ir'
~
,...
I
WIthout Cadi
r---
~
I I
Cadi" 10 pF
80
0
-
'-.....
60
w
~
~
~
-z
80
r---r-
-20
-15
40
~
~
VI" -15 V
20 r-- Vo"-:OV
I" 120 Hz
r-- T =25°C
-25
-30
j r
o
-40
-35
I
0.1
001
10 , OUTPUT
Vo, OUTPUT VOLTAGE (VI
FIGURE 13 - RIPPLE REJECTION VS. FREQUENCY
1
CURRENT (AI
10
FIGURE 14 - OUTPUT IMPEOANCE
100
~
6
~
80
./.
~
60
~
~
COld] '" 10 pF
""-
Without Cadi"\.
40
~
r......
""'"
~
w
'\
VI" - t5 V
20 r--V O "-IDV
r---IL "500 mA
TJ " 25 u c
o
10
VI" -15 V
VO --l0V
IL "500 mA
Cl " lpF
TJ - 25°C
'\.
.......
'\.
~
Cad] - 10,uF
10- 3
1M
lOOK
10K
I, FREQUENCY (Hzl
lK
100
"
'"
10M
w
0:'"
,...>
0 2
,...,...
>"
",0:
~-
.8
4
2
0
~
-0. 2
0:
~;;
-0. 4
0-
>w
~~
~ 23
-0 .5
~-
-1. a
0
A
J
Wllhout Cadi
f\\
,,,
-I
' \ Cadi "110 pF
:nI
\
,,'"
0.2
~>
"'w
6
>
<1
\
/'\
1 \
~~
00
-0.2
,...
~
-0.5
O~
S~ -1.0
40
-2J
-1.5
I
Without Cadi
\ I
\-- I
'-'"
I
~
\
\
vl"-15V
VO"-IOV
INL "SOmA
TJ" 25°C
C\"l P F
1
10
202
'-
\Cadi - 10 pFI
-0.4
~
VO"-10V
IL" 50mA
TJ " 25°C
CL" 1 pF
10
0.6
0.4
-0.6
30
1M
lOOK
FIGURE 16 - LOAD TRANSIENT RESPONSE
FIGURE 15 - LINE TRANSIENT RESPONSE
6
10K
1K
I, FREQUENCY (Hzl
100
10
/
/
V
30
40
LM137, LM237, LM337
APPLICATIONS INFORMATION
BASIC CIRCUIT OPERATION
The LM137 IS a 3-termlnal floating regulator. In operation, the LM137 develops and maintains a nomlnal-1 25
volt reference (Vref) between ItS output and adjustment
terminals. This reference voltage is converted to a programming current (lpROG) by R1 (see Figure 17). and
this constant current flows through R2 from ground. The
regulated output voltage is given by:
returned near the load ground to provide remote ground
sensing and Improve load regulation
EXTERNAL CAPACITORS
A 1 Jl.F tantalum Input bypass capacitor (C ,n ) IS recommended to reduce the sensitivity to Input line Impedance
The adjustment terminal may be bypassed to ground to
Improve ripple re]ectlon. ThiS capacitor (Cad]) prevents
ripple from being amplified as the output voltage IS
Increased A 10 Jl.F capacitor should Improve ripple
re]ectlon about 15 dB at 120 Hz In a 10 volt application
An output capacitor (Co) In the form of a 1 Jl.F tantalum
or 10 Jl.F aluminum electrolytiC capacitor IS required
for stability
Since the current into the adjustment terminal (lad])
represents an error term in the equation, the LM137 was
designed to controlladj to less than 100 Jl.A and keep It
constant. To do thiS, all quiescent operating current is
returned to the output terminal. This Imposes the requirement for a minimum load current. If the load current IS
less than thiS minimum, the output voltage will increase.
PROTECTION DIODES
When external capacitors are used With any I C regulator It IS sometimes necessary to add protection diodes to
preve nt the capacitors from dlscharg I ng th roug h low
current POints Into the regulator
Figure 18 shows the LM137 With the recommended
protection diodes for output voltages In excess of -25 V or
high capacitance values (Co> 25 Jl.F, Cad) > 10 Jl.F)
Diode D1 prevents Co from discharging thru the I C
dUring an Input short CirCUit Diode D2 protects against
capacitor Cad] discharging through the I C dUring an
output short circuit. The combination of diodes D1 and
D2 prevents Cad] from discharging through the I C. dUring
an Input short CirCUit
Since the LII.1137 IS a floating regulator, It IS only the
voltage differential across the CirCUit that IS Important
to performance, and operation at high voltages with
respect to ground IS possible
FIGURE 17 - BASIC CIRCUIT CONFIGURATION
,
-J,
~
+R2
ladl
Ad,ust
V ,n
LM137
,
'pROG
;
I'
Vre !
R1
a
C
\
I
vaut
FIGURE 18 - VOLTAGE REGULATOR WITH
PROTECTION DIODES
IV \.
out
V re !
= -1
25 V Typically
LOAD REGULATION
The LM 137 IS capable of providing extremely good
load regulation, but a few precautions are needed to
obtain maximum performance. For best performance, the
programming resistor (R1) should be connected as close
to the regulator as possible to minimize line drops which
effectively appear In series with the reference, thereby
degrading regulation. The ground end of R2 can be
D1
1N4002
203
LM137M
LM237M
LM337M
@ MOTOROLA
Specifications and Applications
Information
MEDIUM-CURRENT
3-TERMINAL
ADJUSTABLE NEGATIVE
VOLTAGE REGULATOR
3-TERMINAL ADJUSTABLE
OUTPUT NEGATIVE VOLTAGE REGULATOR
The LM137M/237M/337M are adjustable 3-terminal negative
voltage regulators capable of supplying in excess of 500 mA over an
output voltage range of -1.2 Vto -37 V. These voltage regulators are
exceptionally easy to use and require only two external resistors to
set the output voltage. Further, they employ internal current
limiting, thermal shutdown and safe area compensation, making
them essentially blow-out proof.
The LM 137M series serve a wide variety of applications including
local, on-card regulation. This device can also be used to make a
programmable output regulator; or, by connecting a fixed resistor
between the adjustment and output, the LM137M series can be
used as a precision current regulator.
•
Output Current in Excess of 500 mA
•
Output Adjustable Between -1.2 V and -37 V
•
Internal Thermal Overload Protection
•
Internal Short-Circuit-Current Limiting
•
Output Transistor Safe-Area Compensation
•
Floating Operation for High Voltage Applications
SILICON MONOLITHIC
INTEGRATED CIRCUIT
R SUFFIX
METAL PACKAGE
CASE 80
(TO-66 Type)
(Bottom View)
Case is input
Pins 1 and 2 electrically isolated from case.
Case is third electrical connection.
•
Standard 3-Lead Transistor Packages
•
Eliminates Stocking Many Fixed Voltages
T SUFFIX
PLASTIC PACKAGE
(LM337M only)
CASE 221A
(TO-220)
STANDARD APPLICATION
Co **
I "F
Adjust
Vin
Pin 3 Vout
-Yin
0--.-CH
~~~~-~~-----<>-Vout
Heatsink surface connected
to Pin 2
·Cin is required if regulator is located more than 4 inches from power supply
filter. A 1 ~F solid tantalum or 10 JAF aluminum electrolytic is recommended.
-*C o is necessary for stability. A 1 J.AF solid tantalum or 10 IJ.F aluminum electrolytic is recommended.
R2
Vout =-1.25V(1 +R1)
204
ORDERING INFORMATION
Device
LM137MA
LM237MA
LM337MA
LM337MT
Temperature Range
TJ -
55°C to +150oC
25°C to +150oC
TJ TJ - OOC to +125°C
TJ
OOC to +125°C
Package
Metal Power
Metal Power
Metal Power
Plastic Power
LM137M, LM237M, LM337M
MAXIMUM RATINGS
Rating
Input-Output Voltage. Differential
Svmbol
Value
Unit
VI-Va
40
Vdc
Po
Internally Limited
TJ
-55 to +150
-25 to +150
o to +125
°C
Tstg
-65 to +150
°C
Power Dissipation
Operating Junction, Temperature Range
LM137M
LM237M
LM337M
Storage Temperature Range
ELECTRICAL CHARACTERISTICS
IIVI- Vol = 5.0 V. 10 = 0.1; TJ = Tlow to Thigh [see Note 1). Pmax per Note 2.
unless otherwise specified.)
Characteristic
Figure
Symbol
Line Regulation INote 3)
TA = 25°C. 3.0 V"; lVI-Vol,,; 40 V
1
Regline
Load Regulation INote 3).
TA = 25°C. lOrnA"; 10"; 0.5 A
IVai,,; 5.0V
IVai;;. 5.0V
2
Regload
Thermal Regulation
10 mS Pulse. TA = 25°C
-
LM137M/237M
Min
Typ
Max
Min
LM337M
Typ
Max
Unit
0.01
0.02
-
0.01
0.04
%/V
-
15
0.3
25
0.5
-
15
0.3
50
1.0
mV
%VO
Regtherm
-
0.002
0.02
-
0.003
0.04
%VO/W
-
3
lad'
-
65
100
-
65
100
J'A
1.2
61adj
-
2.0
5.0
-
2.0
5.0
J'A
Reference Voltage INote 4)
3.0V,,;IVI-Vol";40V.10mA";10,,;0.5A.
PO"; Pmax . TA = 25°C
Tlow to Thigh
Line Regulation INote 3)
3.0 V"; lVI-Vol ,,; 40 V
3
Vref
-1.250
-1.25
-1.275
-1.30
-1.213
-1.20
-1.250
-1.25
-1.287
-1.30
1
Regline
-
0.02
0.05
-
0.02
0.07
%N
Load Regulation INote 3)
10 rnA"; 10";0.5A
IVoI,,; 5.0 V
IVai;;. 5.0 V
2
Regload
-
20
0.3
50
1.0
-
-
20
0.3
70
1.5
mV
%VO
Temperature StabilitylTlow"; TJ"; Thigh)
3
TS
-
0.6
-
0.6
-
Minimum Load Current to
Maintain Regulation I lVI-Vol ,,; 10 V)
I lVI-Vol ,,; 40 V)
3
ILmin
%VO
rnA
-
1.2
2.5
3.0
5.0
-
-
1.5
2.5
6.0
10
Maximum Output Current
lVI-Vol,,; 15 v. PO"; Pmax
lVI-Vol = 40 V. PO"; Pmax . TA = 25°C
3
0.5
0.15
0.9
0.25
-
0.5
0.1
0.9
0.25
-
RMS Noise. % of Va
TA= 25°C. 10 Hz";f"; 10kHz
-
-
0.003
-
-
0.003
-
Adjustment Pin Current
Adjustment Pin Current Change
2.5 V"; lVI-Vol ,,; 40 V.
lOrnA"; IL"; 0.5 A.
PO"; Pmax . TA = 25°C
Ripple Rejection. Va = -10 V. f
INote 5)
Without Cadj
Cad' = 10 J'F
= 120 Hz
V
-1.225
-1.20
4
-
A
Imax
N
dB
RR
Long Term Stability. TJ = Thigh INote 6)
TA = 25°C for Endpoint Measurements
3
S
Thermal Resistance Junction to Case
R Package ITO-66)
T Package ITO-220)
-
ReJC
%VO
-
60
-
-
60
66
77
-
66
77
-
-
0.3
1.0
-
0.3
1.0
-
7.0
-
-
7.0
7.0
-
%11.0 k
Hrs.
°C/W
NOTES:
(1) Tlow = -55°C for LM137M
Thigh::: +150 0 C for LM137M
::: -25°C for LM237M
::: +150°C for LM237M
O°C for LM337M
::: +125°C for LM337M
(2) P max =75 W
(3) Loadand Hne regulation are specified atconstantjunctlOn temperature.
Changes In Va due to heating effects must be taken Into account
separately. Pulse testing With low duty cycle is used.
-
(4) Selected devices with tightened tolerance reference voltage available.
(5) Cadi' when used, IS connected between the adjustment pin and ground.
(6) Since Long Term Stability cannot be measured on each deVice before
shipment, this speCificatIOn is an engineering estimate of average
stability from lot to lot.
205
LM137M, LM237M, LM337M
SCHEMATIC DIAGRAM
60
Adjust
100
~
\
2.5k
2k
810
r(lk
L-+-
r"-J
Vout
...-i
~"
5k
J.#
60k
l~
(1
~
...-"
18 k
0
0
a)
t
..
25
of
2k
V
f...
~
J
~
.--r
4k
V
ho.
~6
"~Q
~ H8: f{H::
~O
l{
2.9
k
V
6.0k~
f...
~
100
}r;
600
~
15pP
"
"
15pF
lOOk
220
a)
~
~ 750
0
0
10k
r<
~!.O
100pF
*
k
240
15
2.4k
2.0
pF
0
~
5.0k
lOOk
500
30k
~
5.0 pF
.-1
-"
0
N
4.0
~
18 k
f...
~
H:
'---
O. 2
15
155
500
O.
FIGURE 1 - LINE REGULATION AND
1.5
....
-0.4
'" -1.2
=
-
,...-
~
~
6VO~100mV
2.5
---------
0
~
~
0
2.0
>
....
ii'
55
~
0
50
I
I 5
....
U
----.. ---..
r-- ~
-25
25
50
75
100
TJ• JUNCTION TEMPERATURE 1°C)
125
0
> 1.0
150
-50
-25
:>
25
.5
~
--
~
~ 1.240
0:
i3
I-
i
1.6
25
50
75
100
~
125
150
125
--
~
,
TJ ~ 150 aC
~
0.8
o
/'
~/
"..
1.0
V
c:!
TJ.JUNCTION TEMPERATURE 1°C)
f-
j
:5 0.6
150
-55°C
1.2
0.2
-25
100
TJ~25aC
1.4
_ri::J 0.4
-50
T)
-
1.8
w
75
"i
FIGURE 10 - MINIMUM OPERATING CURRENT
;;;0
1.250
50
~20ImA""""
TJ. JUN CTiO N TEMPE RA TU RE 1°C)
FIGURE 9 - TEMPERATURE STABILITY
2: 1.260
'"
~
o
IL~500mA
~
IlL
1.270
1.230
IL~~
~
40
i
____
ii'
3- 45
-50
40
30
v~ = -5'V
~-
.6
>!:!
~!C 0.2
2
0
~
«
'"
0.6
.8
.4
-0. 2
.I
Il
Without Cadi
lfi \
"',
::oW
..
~
\
>w
~~
~~
-0. 5
~
-1.0
0
....
z
W
-0.5
00:
~~ -1.0
-' u
30
20
t, TIME
..:.
40
I~~
209
-1.5
_. /
V'
I
>
3
\
Cadi = 10 ~F
-0.4
-0.6
VO=-IOV
IL=50mA
TJ = 25°C
CL = I ~F
10
-0.2
I
.I
c.di =110 ~F
.......... 1\
0:4
00
.\
~> -0.4
0-
2
0
/1
1M
lOOK
10K
IK
f, FREQUENCY 1Hz)
100
10
~
~
\
VI =-15V
VO=-IOV
INL = 50 mA
TJ = 250 C
C~ = I ~FI
10
20
t, TIME I"~
I
/
/
3D
40
LM137M, LM237M, LM337M
APPLICATIONS INFORMATION
BASIC CIRCUIT OPERATION
The LM137M is a 3-terminal floating regulator. In
operation, the LM 137M develops and maintains a nominal -1.25 volt reference (Vretl between its output and
adjustment terminals. This reference voltage is converted
to a programming current (lpROG) by Rl (see Figure 17).
and this constant current flows through R2 from ground.
The regulated output voltage is given by:
returned near the load ground to provide remote ground
sensing and improve load regulation.
EXTERNAL CAPACITORS
A 1 !iF tantalum input bypass capacitor(Cin) is recommended to reduce the sensitivity to input line impedance.
The adjustment terminal may be bypassed to ground to
improve ripple rejection. This capacitor (Cadj) prevents
ripple from being amplified as the output voltage is
increased. A 10!iF capacitor should improve ripple
rejection about 15 dB at 120 Hz in a 10 volt application.
An output capacitor (Co) in the form of a 1 !iF tantalum
or 10!iF aluminum electrolytic capacitor is required
for stability.
R2
Vout = Vref (1 + R1) + ladjR2
Since the current into the adjustment terminal (ladj)
represents an error term in the equation, the LM137M
was designed to contro"adj to less than 1OO!iA and keep
it constant. To do this. all quiescent operating current is
returned to the output terminal. This imposes the requirement for a minimum load current. If the load current is
less than this minimum, the output voltage will increase.
Since the LM137M is a floating regulator, it is only the
voltage differential across the circuit that is important to
performance, and operation at high voltages with respect
to ground is possible.
PROTECTION DIODES
When external capacitors are used with any I.C. regulator it is sometimes necessary to add protection diodes to
prevent the capacitors from discharging through low
current points into the regulator.
Figure 18 shows the LM 137M with the recommended
protection diodes for output voltages in excess of -25 Vor
high capacitance values (Co> 25 !iF. Cadj > 10 !iF).
Diode Dl prevents Co from discharging thru the I.C.
during an input short circuit. Diode D2 protects against
capacitor Cadj discharging through the I.C. during an
output short circuit. The combination of diodes Dl and
D2 prevents Cadj from discharging through the I.C. during
an input short circuit.
FIGURE 17 - BASIC CIRCUIT CONFIGURATION
+
-=1-
-
t R2
ladJ
AdJustl
Vin
LM137M
IpROG
;'
Vre!
I\
RI
+
Co
\
I
vout
FIGURE 18 - VOLTAGE REGULATOR WITH
PROTECTION DIODES
VOU!
Vre!
c
-1.25 V TYPIcally
Co
LOAD REGULATION
The LM137M is capable of providing extremely good
load regulation, but a few precautions are needed to
obtain maximum performance. For best performance, the
programming resistor (Rl) should be connected as close
to the regulator as possible to minimize line drops which
effectively appear in se'ries with the reference, thereby
degrading regulation. The ground end of R2 can be
D2
DI
IN4002
210
VOU!
®
LM140 series
LM340 series
MOTOROLA
THREE-TERMINAL
POSITIVE
FIXED VOLTAGE
REGULATORS
3-TERMINAL POSITIVE VOLTAGE REGULATORS
The LM 140/340 series of three-terminal positive voltage
regulators are monolithic integrated circuits designed for a wide
variety of applications including local on-board regulation. Available in seven fixed output voltage options from 5.0 to 24 volts,
these regulators employ internal current limiting, thermal shutdown, and safe area compensation - making them virtually blowout proof. The LM140/340 series is guaranteed to have line and
load regulation that is a factor of two better than the 7800 series.
Although the LM140/340 series was designed primarily as a fixed
regulator, it can be used with external components to obtain
adjustable voltages.
•
Output Currents in Excess of 1.0 A
•
Internal Thermal Overload Protection
•
Internal Short Circuit Limiting
•
Output Transistor Safe-Area Compensation
K SUFFIX
METAL PACKAGE
CASE 1
ITO·3 TYPE)
(bottom view)
•
No External Components Required
•
Available in Both Commercial and MilitaryTemperatureRanges
PinS' and 2 electrically isolated from case, Case
is third electrical connection.
STANDARD APPLICATION
ORDERING INFORMATION
Device
Voltage
LM140K-5.0
LM140K-6.0
LM140K-8.0
LM140K-12
LM140K-15
LM140K-18
LM140K-24
5.0
6.0
8.0
12
15
18
24
Volts
Volts
Volts
Volts
Volts
Volts
Volts
LM340K-5.0
LM340K-6.0
LM340K-8.0
LM340K-12
LM340K-15
LM340K-18
LM340K-24
5.0 Volts
6.0 Volts
8.0 Volts
12 Volts
15 Volts
18 Volts
24 Volts
Temperature Range (TAl
-55
-55
-55
-55
-55
-55
-55
to
to
to
to
to
to
to
+125°C
+125°C
+125°C
+125°C
+125°C
+125°C
+125°C
o to +70 oC
o to +70°C
o to +70 oC
o to +70°C
o to +70 oC
o to +70°C
o to +70 oC
A common ground is required between
the input and the output voltages. The input
voltage must remain typically 2.0 V above
the output voltage even during the low
point on the input ripple voltage.
*
regulator is located an appreciable
distance from power supply filter.
**
211
= Cin (solid tantalum) is required, if
= Co
is not needed for stability;
however, it does improve transient
response, If needed, its value should
be greater than 0.1 I'F.
LM140 Series, LM340 Series
LM140 series/LM340 series
MAXIMUM RATINGS (TA = +25°C unless otherwise noted.)
Rating
Value
Symbol
Input Voltage
(5.OV-18 V)
(24 V)
Unit
Vdc
Vin
35
40
Power Dissipation and Thermal Characteristics
(Metal Package)
TA = +25 O C
Derate above TA = +25°C
Thermal Resistance. Junction to Air
TC = +25 O C
Derate above TC = +65 0 C (See Figure 2)
Thermal Resistance. Junction to Case
Storage Junction Temperature Range
Operating Junction Temperature Range
LM140
LM340
Po
l/RBJA
RIlJA
Po
l/RIIJC
RBJC
Internally Limited
22.5
45
Internally Limited
182
5.5
Tstg
-65 to +150
Watts
mW/oC
°CIW
Watts
mW/oC
°CIW
°c
°c
TJ
-55 to +150
to +125
o
NOTES:
1. Tlow = -55°C for LM140
Thigh = +150 oC for LM140
= OoC for LM340
= +125°C for LM340
2. Losd and line regulation are specified at constant junction temperature. Changes in Vo due to heating effects must be taken into
account separately. Pulse testing with low duty cycle is used.
212
LM140 Series, LM340 Series
LM140/340 - 5.0
(Vin
ELECTRICAL CHARACTERISTICS
= 10 V, 10 =500 mA. TJ =Tlow to Thigh (Note 1), unless otherwise noted).
Characteristic
Output Voltage (TJ =+25°q
10 = 5.0 mA to 1.0 A
Input Regulation (Note 2)
8.0 to 20 Vdc
7.0 to 25 Vdc (TJ =+25°C)
8.0 to 12 Vdc, 10 = 1.0 A
7.3 to 20 Vdc, 10 = 1.0 A (TJ
Min
Typ
Max
Unit
Vo
4.8
5.0
5.2
Vdc
-
-
50
50
25
50
Regin
=+25°q
-
Load Regulation (Note 2)
5.0 mA ~ 10 ~ 1.0 A
5.0 mA ~ 10 ~ 1.5 A (TJ =+25°C)
250 mA ~ 10 ~ 750 mA (TJ =+25°q
Regload
-
-
Output Voltage
LM140
8.0~ Vin ~ 20 Vdc, 5.0 mA~ 10 ~ 1.0A,
PO~ 15 W
LM340
7.0 ~ Vin ~ 20 Vdc, 5.0 mA ~ 10 ~ 1.0 A.
PO~ 15 W
mV
-
mV
50
50
25
Vdc
Vo
Quiescent Current
10 = 1.0A
LM140
LM340
LM140 (TJ =+25 O C)
LM340 (TJ =+25°q
4.75
5.0
5.25
4.75
5.0
5.25
4.0
4.0
4.0
4.0
7.0
8.5
6.0
8.0
-
0.8
1.0
0.5
0.8
1.0
mA
Ib
-
-
-
Quiescent Current Change
8.0 ~ Vin ~ 25 Vdc
7.0 ~ Vin ~ 25 Vdc
5.0 mA~ 10 ~ 1.0 A
8.0 ~ Vin ~ 20 Vdc, 10 = 1.0 A
7.5 ~ Vin ~ 20 Vdc, 10 = 1.0 A
alb
LM140
LM340
LM140, LM340
LM140
LM340
Ripple Rejection
LM140
LM340
10 = 1.0 A (TJ =+25°C)
LM140
LM340
Dropout Voltage
Vin - Vo
RO
Short-Circuit Current Limit
Output Noise Voltage (TA
10Hz ~ f ~ 100kHz
mA
-
-
-
-
68
62
80
80
68
62
-
-
-
2.0
-
Vdc
30
-
m!l.
-
dB
RR
Output Resistance
=+25°C)
Average Temperature Coefficient of Output Voltage
10 = 5.0 mA
Peak Output Current (TJ
Symbol
=+25°C)
Input Voltage to Maintain Line Regulation (TJ
10 = 1.0A
-
-
Ise
-
2.0
Vn
-
40
-
p.V
TCVO
-
±0.6
-
mV/oC
-
2.4
7.3
-
-
Vdc
10
=+25°C)
-
A
A
NOTES:
1. Tlow = -55°C for LM140
Thigh = +150 0 C for LM140
= 0° C for LM340
= +1 25°C for LM340
2. Load and line regulation are specified at constant junction temperature. Changes in Vo due to heating effects must be taken into
account separately. Pulse testing with low duty cycle is used.
213
LM140 Series, LM340 Series
LM140/340 -
6.0
ELECTRICAL CHARACTERISTICS
(Vin = 11 V, 10 = 500 mA. TJ = T,ow to Thigh (Note 1), unless otherwise noted).
Cheracteridic
Output Voltage ITJ = +25 O C)
'0 = 5.0 mA to 1.0 A
Symbol
Min
Typ
Mex
Unit
Vo
5.75
6.0
6.25
Vdc
-
-
60
60
-
-
60
Input Regulation INote 2)
9.0 to 21 Vdc
8.0 to 25 Vdc ITJ = +25°C)
9.0 to 13 Vdc, '0 = 1.0 A
8.3 to 21 Vdc, '0 = 1.0 A ITJ = +25°C)
Regin
Load Regulation (Note 2)
5.0 mAos;; '0 OS;; 1.0 A
5.0 mA EO; '0 EO; 1.5 A ITJ = +25°C)
250 mA EO; 10 EO; 750 mA ITJ = +25°C)
Regload
Output Voltage
LMI40
9.0 EO; Vin EO; 21 Vdc, 5.0 mA EO; '0 OS;; 1.0 A,
POEO;15W
LM340
8.0 EO; Vin EO; 21 Vdc, 6.0 mAEO;loEO; 1.0A,
POEO;15W
30
60
mV
-
-
60
30
5.7
6.0
6.3
5.7
5.0
6.3
-
4.0
4.0
4.0
4.0
7.0
8.5
6.0
8.0
-
-
0.8
1.0
0.5
0.8
1.0
Vdc
Vo
Quiescent Current
10= 1.0A
LMI40
LM340
LMI40 ITJ = +25°C)
LM340 ITJ = +25 O C)
Quiescent Current Change
g.O EO; Vin EO; 25 Vdc
8.0 EO; Vin EO; 25 Vdc
5.0 mA EO; '0 EO; 1.0 A
9.0 EO; Vin EO; 21 Vdc, 10 = 1.0 A
8.6 EO; Vin EO; 21 Vdc, 10 = 1.0 A
mV
mA
Ib
-
....
50
.......'"
'"
'\.
~
-25
0
r\.
6HS = 100CM
-.....
No Heat Sink
75
6.0
w
'\
0
LJ140K.~.0
I- TJ = 250C
6HS= 0
0
IOUI=10m~
TA. AMBIENT TEMPERATURE (DC)
~
~~
.... 0
~~
1.5
W W
g
3.5
~
r--
~
10= 1.0A
r--
~
I--
"'<
~~
"'w
~ ~ 1.0
-- --t---+I-
'0
'"
~
iii
J500 mA
3.0
2. 5
R
~ 2. 0
,
~
1. 5
~
1.0
o
TJ = 25 0C' \
0.5
-25
25
50
75
100
o
125
TA. AMBIENT TEMPERATURE 10C)
~
r "
TJ = 1250C'
0.5
-50
,TJ = -55 0C
'{ ,~
~
10= 10mA
6!::!:::
>0
.;;
W
AV OUI =100mA
_
_ 2.0
~
FIGURE 4 - PEAK OUTPUT CURRENT AS A FUNCTION
OF INPUT·OUTPUT DIFFERENTIAL VOLTAGE
w
~
~
INPUT VOLTAGE (V)
FIGURE 3 - INPUT·OUTPUT DIFFERENTIAL
ASA FUNCTION OF JUNCTION TEMPERATURE
2.5
UI = 500 mA
)~!,OU! =11.0 A
o
o u
125
,
/I/" 'i
2.0
I Iu
:::::
100
4.0
o
~~
~~
5.0
10
15
20
25
30
35
Vin - VO.INPUT/OUTPUT VOLTAGE
DIFFERENTIAL (VOLTS)
FIGURE 5 - RIPPLE REJECTION
AS A FUNCTION OF FREQUENCY
FIGURE 6 - QUIESCENT CURRENT
AS A FUNCTION OF TEMPERATURE
0
.
10-
:s
z
o
;(
tw
;;]
'"w
~ 40
ra:
r'"
","
20
10
..s....
'"
0
100
r-...
w
'"'"
'"
<>
....
3.0
'"w
2.0
iii
<>
Vin' 8.0 10 18 Vdc
VO' 5.0 V
IO = 1.0A
Tt~iiilll
LIIIW
-
4.0
z
Vin=10V
VOU! = 5.0 V
10UI= 5.0 mA
""'-
........
:;
0
'"
1.0k
f. FREQUENCY (Hz)
10 k
1.0
-50
100 k
220
25
50
75
-25
TA. AMBIENT TEMPERATURE (DC)
100
125
®
LM150
LM250
LM350
MOTOROLA
Advance Information
3-TERMINAL
ADJUSTABLE POSITIVE
VOLTAGE REGULATOR
3-TERMINAL ADJUSTABLE
OUTPUT POSITIVE VOLTAGE REGULATOR
The LM150/250/350 are adjustable 3-terminal positive voltage
regulators capable of supplYing in excess of 3.0 A over an output
voltage range of 1.2 V to 33 V. These voltage regulators are exceptionally easy to use and require only two external resistors to set the
output voltage. Further, they employ internal current limiting,
thermal shutdown and safe area compensation, making them
essentially blow-out proof.
The LM150 series serve a wide variety of applications including
local, on card regulation. This device also makes an especially
Simple adjustable switching regutator, a programmable output
regulator, or by connecting a fixed resistor between the adjustment
and output, the LM 150 series can be used as a precision current
regulator
SILICON MONOLITHIC
INTEGRATED CIRCUIT
K SUFFIX
METAL PACKAGE
CASE 1
(TO-3 Type)
•
Guaranteed 3.0 Amps Output Current
•
Output Adjustable between 1.2 V and 33 V
•
Load Regulation Typically 0.1 %
(Bottom View)
•
Line Regulation Typically 0 005%/V
•
Internal Thermal Overload Protection
•
Internal Short-Circuit Current Limiting Constant with Temperature
•
Output Transistor Safe-area Compensation
•
Floating Operation for High Voltage Applications
•
Standard 3-lead Transistor Packages
•
Eliminates Stocking Many Fixed Voltages
Pins 1 and 2 electrically Isolated from case.
Case is third electrical connectIOn.
STANDARD APPLICATION
v
'n
v out
LM15D
iAdll
~
f",
CASE 221 A
(TO-2201
240
Adjust
*
r:"c
T SUFFIX
PLASTIC PACKAGE
**
r
c
~~2
I
1
Pin 1
Pin 2
•
Pm 3
Heatsmk su rface connected
to Pin 2
-=-
*
=
**
=
Cin is required if regulator is located an appreciable distance from power
sup pI .... filter.
Co is not needed for stability, however it does improve transient
response.
V out = 1,25V (1
R2
+-l +
IAdj R2
R,
Since IAdj is controlled to less than 100 /.lA, the error associated with this
term is negligible in most applications
221
Adjust
V out
Vin
ORDERING INFORMATION
Package
Device
Temperature Range
LM150K
LM250K
TJ=-55°Cto+150°C
TJ = -25°C to +150oe
Metal Power
LM350K
TJ:= oDe to +125°e
Metal Power
LM350T
TJ:= O°C to +125°e
PlastiC Power
Metal Power
LM150, LM250, LM350
MAXIMUM RATINGS
Rating
Input-Output Voltage Differential
Power Dissipation
Operating Junction Temperature Range
Symbol
Value
Unit
V'-Va
Po
35
Vdc
LM150
LM250
LM350
Storage Temperature Range
Internally Limited
TJ
-55 to +150
-25 to +150
to +125
°C
-65 to +150
°C
300
°C
o
Tstg
Soldering Lead Temperature (10 seconds)
ELECTRICAL CHARACTERISTICS (Unless otherwise specilied, V,-VO= 5 V; 'L = 1.5 A; TJ= T'owto Thigh[see Note 1]; Pmax= 30W)
Figura
Symbol
Line Regulation (Note 2)
TA = 25°C, 3 V';' V, - Va';' 35 V
1
Regline
Load Regulation (Note 2)
TA = 25°C, 10 rnA';' 'L';' 3A
VO';'5V
Va;' 5 V
2
Regload
Thermal Regulation Pulse = 20 ms
-
Adjustment Pin Current
3
Characteristic
Min
-
-
%/W
-
-
5
0.1
Regtherm
-
0.002
-
0.002
'Ad·
LlIAdj
-
50
100
-
50
100
-
0.2
5
-
0.2
5
1.25
1.30
1.20
1.25
1.30
-
0.02
0.05
-
0.02
0.07
-
20
0.3
-
20
0.3
70
1.5
mV
%VO
-
1
50
1
-
-
1
-
%VO
rnA
-
3.5
5
-
3.5
10
3.0
0.3
4.5
1
-
3.0
0.25
4.5
1
-
-
0.003
-
-
0.003
-
-
-
-
66
65
80
66
65
80
-
-
0.3
-
0.3
1
2
Temperature Stability (T,ow';' TJ';' Thigh)
Minimum Load Current to
Maintain Regulation (VI-Va = 35 V)
3
TS
3
'Lmin
Maximum Output Current
V'-Va';' 10V, Po';' Pmax
V'-Va = 30 V, PO';' Pmax , TA = 25°C
RMS Noise, % 01 Va
TA = 25°C, 10 Hz';' I';' 10 kHz
3
-
mV
%VO
15
0.3
Load Regulation (Note 2)
lOrnA';' IL';' 3A
Va';' 5V
Va;' 5 V
Thermal Resistance Junction to Case
Peak (Note 6)
K Package (TO-3)
T Package (TO-220)
Average (Note 7)
K Package (TO-3)
T Package (TO-220)
25
0.5
5
0.1
-
J1.A
J1.A
V
Vrel
1.20
3
%IV
-
3
4
Unit
0.03
0.01
Relerence Voltage (Note 3)
3 V';' V'-Va';' 35 V
lOrnA';' IL';' 3 A. PO';' Pmax
Line Regulation (Note 2)
3V,;,V,-VO.;,35V
Ripple Rejection, Va = 10 V, I = 120 Hz
(Note 4)
Without CADJ
CAOJ = 10 J1.F
Long Term Stability, TJ = Thigh (Note 5)
TA = 25°C lor Endpoint Measurements
Max
0.005
0.005
1,2
-
LM350_
Typ
Min
-
Adjustment Pin Current Change
3 V';' V'-Va';' 35 V
10 rnA';' IL';' 3 A. PO';' Pmax
1
LM150/250
Typ
Max
Regline
%/V
Reg'oad
Imax
N
-
%VO
RR
S
R6JC
A
dB
-
2.3
-
1
1.5
-
-
%/1.0k
Hrs.
°C/W
2.3
2.3
-
-
1.5
1.5
NOTES:
(1) T,ow: -55°C for LM150
Thigh: +IS0oC for LM150
: +150oC for LM250
-25°C for LM2S0
: +125°C for LM350
OOC for LM350
(2) Load and line regulation are specified at constant junction temperature.
Changes in Vo due to heating effects must be taken into account
separately. Pulse tasting with low duty cycle is used.
(3) Selected devices with tightened tolerance reference voltage available.
(4) CADJ. when used. is connected between the adjustment pin and
ground.
{51 Since long Term Stabihty cannot be measured on each deVice before
shipment, this specification is an engineering estimate of average
stability from lot to lot.
(6) Thermal Resistance evaluated measuring the hottest temperature on
the die using an infrared scanner. This method of evaluation yields very
accurate thermal resistance values which arB conservative when
compared to other measurement techniques.
(7) The average die temperature is used to derive the value of thermal
resistance junction to case (average).
222
LM150, LM250, LM350
SCHEMATIC DIAGRAM
0.045
L-~--~----~--4---~~~~~~~--~--'-----t-------~~4-----------------'---~----~Vout
'-_______________________________.---<> Adjust
FIGURE 1 - LINE REGULATION AND alAdj/LlNE TEST CIRCUIT
Vcc
Lme Regulation (%/V)
VOW-VOL
=
VOL
V out
LM150
Adjust
0.1 p.F
1 P.F
* Pulse Testing Required:
1 % Duty Cycle
ISluggested.
223
X 100
~150,Lftn250,Lftn350
FIGURE 2 - LOAD REGULATION AND .o.lAdj/LOAD TEST CIRCUIT
Load Regulation (mV) = Vo (min. Load) - Vo (max. Load)
Load Regulation (%VO) = Vo (min. Load) - Vo (max. Load) X 100 L J v V o (min. Load)
V out
LM150
Vo (min. Load)
Vo (max. Load)
IL
RL
(max. Load)
240
1%
Adjust
RL
(min. Load)
O.lI'F
*
Pulse Testing Required:
1 % Duty Cycle is suggested.
FIGURE 3 - STANDARD TEST CIRCUIT
V out
LM15Q
240
1%
O.lI'F
To Calculate A 2 :
Pulse Testing Required:
1 % Duty Cvcle I. suggested.
Vo = ISET R2 + 1.250 V
Assume 'SET"" 5.25 rnA
FIGURE 4 - RIPPLE REJECTION TEST CIRCUIT
24V-"
.
14V----V
V out
Vln
Vo = 10 V
LM150
f = 120 Hz
IL
Adjust
Rl <
240
1%
01"
r-
.... lN4002
RL
+
Cln
;:i'
0.1 I'F
Co:::r: 11'F
R2
-'-
1.65 K
1%
1+
CAOJ
;~~
10 pF
1
1
* 0,
Discharges CADJ .f Output
224
15
Shorted to Ground.
Vo
LM150, LM250, LM350
FIGURE 5 - LOAD REGULATION
~
0.4
z
0.2
w
to
g
~
IL
w
to
""':3
>
IL
-0.4
~
0
-0.6
0
>
~
~
--
V
40
..-
'.'\,.' ,
0
I
25
50
75
100
125
---
:----.
~
:----.
r.::r- --r---.
.
--
..
IL! 3.0 A
~---
IL
~
----
2.0 A
f----- . - -
r- ;::-- -:: r---
1.5
-
.-
1----- - - -
~
r--... :----.
IL
-~500mA
(---:
-c~200mA
~ ~OmA
>°1.0
150
f-~l
6V O ~ 100 mV
~;;::
-25
40
FIGURE 8 - DROPOUT VOLTAGE
3.0
i=
-I-
-
--
60
2
a:
~
-.-
65
'"
'"
::>
u
\'
" r--:.: ----
-;:;
r;j'
-
1500C-
I
FIGURE 7 - ADJUSTMENT PIN CURRENT
.3
TJ~
it
"""
0
25
50
75
100
125
TJ. JUNCTION TEMPERATURE lOCI
TJ~250C
l!
Ji
--
~1.5A/ f<;: ...........
I
...... _ TJ'" -55°C
rt---
1--
IL ~3.0A/
VI ~ 15 V
f--VO~lOV
I-
::>
.r-- -
~500mA
r-- f:::::+-..
-0.2
0
I-
FIGURE 6 - CURRENT LIMIT
-75
-50
-25
25
TJ. JUNCTION TEMPERATURE lOCI
50
75
100
125
150
TJ• JUNCTION TEMPERATURE (oCI
FIGURE 9 - TEMPERATURE STABILITY
FIGURE 10 - MINIMUM OPERATING CURRENT
1.260
5.0
4.5
:;
:;; 1.250
to
V
""':3
o
>
r- ~
!---
;j' 4.0
...........
~ 1.240
i
~
~
3.0
::>
u
2.5
I-
T/~ 25 0C- 2
2
-
~ 2.0
--
3 1.5
i; 1.230
~1.0
0.5
-50
-25
25
50
75
100
125
o
150
TJ.JUNCTION TEMPERATURE lOCI
:;;;: ~
'1 .........;.::- 'f7~
~1500C
f:::::= ~
d
>~
1.220
-75
TJ ~ -55°C
5
~ 3.5
II
o
10
20
30
V I - VO' INPUT - OUTPUT VOLTAGE DIFFERENTIAL IVdcl
225
40
LM150, LM250, LM350
FIGURE 12 - RIPPLE REJECTION VS. OUTPUT CURRENT
FIGURE 11 - RIPPLE REJECTION VS OUTPUT VOLTAGE
100
CAOJ = 10pF
"
~
'I'--.
Z
~
0
§
120
80
60
;;J
-
"'
~ 100
Z
WITHOUT CAOJ
o
--
~
~
~
w
~
~
"'
~
~
40 f - - -
~
VI - V r 5V
IL =50 mA
t = 120 Hz
TJ = 25°C
f--20 f - - -
~
o
VI = 15 V
VO=IOV
t=120Hz
TJ = 25°C
40
~
I
o
60
!l;
~
10
30
15
20
25
VO' OUTPUT VOLTAGE (V)
~
~
~
!l;
WITHb~c'AOJ,
1
I
0.01
0.1
10
10, OUTPUT CURRENT (A)
FIGURE 14 - OUTPUT IMPEDANCE
10 1
80
/
---
// ~
60
V
t--~
40
~
~.
20
I
~ =500mA
w
~
~ I
r-
o
35
FIGURE 13 - RIPPLE REJECTION VS. FREQUENCY
Z
CAor IOpF
r-
20
100
0
-
80
1= 15V
Vo = 10 V
TJ = 25°C
'\
~
r------
~
r-----
10 0
~
15 V
-10 V
500mA
25°C
1
1
lK
10K
WITHOUT CAOJ
CAOJ
"'"--
=10 pF
o
100
VI
Va
IL
TJ
-
\
I"\. \
\ 1\
WITHOUT CAOJ
10
==
lOOK
1M
10-3
10
10M
100
lK
FIGURE 15 - LINE TRANSIENT RESPONSE
1
0
5
0
CL =lpF;C AOJ =10pF
It\.
Vo = 10 V
~ =50mA
J = 25°C
-
--
1
-J
5
20
t,
30
_ 1.5
~
Jl
'" 1.0
0I-
«
oZ
I
i
10
!/
\
'-',
I
I
\
I
.I CAOJ VI = 15 V
\ /' ~.CL =10; WITHOUT
f--- VO=IOV
\I
CL = 0; WITHOUT CAOJ
0
I
\
1
t/
-- VA\.
-
5
0
/
J.
"
1M
f\
1
~
I
_ C L =lpF;C AOJ =lOpF
0
lOOK
FIGURE 16 - LOAD TRANSIENT RESPONSE
5
5
10K
t, FREQUENCY (Hz)
t, FREQUENCY (Hz)
~O.5
-=>
u
40
~L =50mA
J = 25°C
;>
I
1\
/
I'
\.
0
20
t, TIME (ps)
226
f-----
'\'" JL
10
TIME (ps)
-f-----
30
40
LM150, LM250, LM350
APPLICATIONS INFORMATION
BASIC CIRCUIT OPERATION
The LM150 is a3-terminal floating regulator. In operation, the LM 150 develops and maintains a nominal 1.25
volt reference (V refl between its output and adjustment
terminals. This reference voltage is converted to a pro·
gramming current (lpROGI by Rl (see Figure 171, and
this constant current flows through R2 to ground. The
regulated output voltage is given by:
EXTERNAL CAPACITORS
A 0.1 J1F disc or 1 J1F tantalum input bypass capacitor
(Cinl is recommended to reduce the sensitivity to input
line impedance.
The adjustment term inal may be bypassed to ground to
improve ripple rejection. This capacitor (CADJI prevents
ripple from being amplified as the output voltage is
increased. A 10 J1F capacitor should improve ripple
rejection about 15dB at 120 Hz in a 10 volt application.
Although the LM 150 is stabre with no output capaci·
tance, like any feedback circuit, certain values of external
capacitance can cause excessive ringing. An output capaci·
tance (Col in the form of a 1 J1F tantalum or 25 J1F
aluminum electrolytic capacitor on the output swamps
this effect and insures stability.
R2
Vout ~ Vref (1 + Rl"1 + IAdj R2
Since the current from the adjustment terminal (IAdjl
represents an error term in the equation, the LM 150 was
designed to control IAdj to less than 100 J1A and keep it
constant. To do this, all quiescent operating current is
returned to the output terminal. This imposes the require·
ment for a minimum load current. If the load current is
less than this minimum, the output voltage will rise.
Since the LM150 is a floating regulator, it is only the
voltage differential across the circuit which is important
to performance, and operation at high voltages with
respect to ground is possible.
PROTECTION DIODES
When external capacitors are used with any I.C. regu·
lator it is sometimes necessary to add protection diodes to
prevent the capacitors from discharging through low
current points into the regulator.
Figure 18 shows the LM 150 with the recommended
protection diodes for output voltages in excess of 25 V or
high capacitance values (Co> 25 J1F, CADJ > 10 /1FI.
Diode 01 prevents Co from discharging thru the I.C.
during an input short circuit. Diode 02 protects against
capacitor CADJ discharging through the I.C. during an
output short circuit. The combination of diodes 01 and
02 prevents CADJ from discharging through the I.C.
during an input short circuit.
FIGURE 17 - BASIC CIRCUIT CONFIGURATION
v'"
LM15Q
I
I
v out
!
\
+
R,
Vref
Adjust
--
FIGURE 18 - VOLTAGE REGULATOR WITH
PROTECTION DIODES
l'PROG
V out
lAd]
R2
Vref = 1.25 V TYPICAL
1
-=-LOAD REGULATION
The LM 150 is capable of providing extremely good
load regulation, but a few precautions are needed to
obtain maximum performance. For best performance, the
programming resistor (R 11 should be connected as close
to the regulator as possible to minimize line drops which
effectively appear in series with the reference, thereby
degrading regulation. The ground end of R2 can be
returned near the load ground to provide remote ground
sensing and improve load regulation.
227
LM150, LM250, LM350
FIGURE 19 - "LABORATORY" POWER SUPPLY WITH ADJUSTABLE
CURRENT LIMIT AND OUTPUT VOLTAGE
IN4002
V out1
Rse
VIN ......--_~~_.J
IN4001
TTL
720
Control
1 K
2N5640
Vref
Al = lOmax + lOSS
VO< BVOSS + 1.25 V+ VSS
< '0 < 3
< '0 < 2 A
'Lmin - lOSS
As shown 0
Minimum V out = 1.25 V
A
01 protects the deVIce dUring an Input short circuit.
FIGURE 23 - CURRENT REGULATOR
FIGURE 22 - SLOW TURN-ON REGULATOR
LM150
Adjust
~
V out
I
Al
I
~
Vref
lout = (Fi1)
+ IAdj
'" 1.26 V
Al
10 rnA " lout" 3 A
228
-lout
@ MOTOROLA
MC1463
MC1563
Specifications and Applications InforIllation
NEGATIVE VOLTAGE REGULATOR
The MC1563/MC1463 is a "three terminal" negative regulator designed to deliver continuous load current up to 500 mAde and provide a maximum negative input voltage of
-40 Vdc. Output current capability can be increased to greater than 10 Adc through use
of one or more external transistors.
Specifications and performance of the MC1563/MC1463 Negative Voltage Regulator are
nearly identical to the MC1569/MC1469 Positive Voltage Regulator. For systems requiring both a positive and negative power supply, these devices are excellent for use as
NEGATIVE-POWER-SUPPL Y
VOLTAGE REGULATOR
SILICON MONOLITHIC
INTEGRATED CIRCUIT
complementary regulators and offer the advantage of operating with a common input
ground.
The MC1563R/MC1463R case can be mounted directly to a grounded heat sink which
eliminates the need for an insulator.
•
Case is at Ground Potential (R package)
•
Electronic "Shutdown" and Short-Circuit Protection
•
Low Output Impedance
•
High Power Capability ~ 9.0 Watts
•
Excellent Temperature Stabil~ty ~ AVO/AT::O ± 0.002%/oC typical
•
High Ripple Rejection ~ 0.002% typical
•
~
20 Milliohms typical
R SUFFIX
G SUFFIX
METAL PACKAGE
CASE 603
500 rnA Current Capabil ity
FIGURE 1 - TYPICAL CIRCUIT CONNECTION
(1-3.sl>(vo>(I-37Ivdc, 1 >(Il. >(500 mAl
METAL PACKAGE
CASE 614
FIGURE 2 - TYPICAL NPN CURRENT BOOST CONNECTION
(VO "5.2 Vdc, I L " 10 Adc (maxI I
GNO
GNo
CASE
68k
RS
RL
lN4001
Co
IL ~
10 A
100
RL
,f
Qr EqlllV
ma~
MCl563R
MC1463R
Vo
Select RA to Give Desired VD
RA" 12 'VD 1-71 Ut
lO ~
50 m,lllohms
Va
-52 Vdc
FIGURE 3 - ±.15 V. ±.400 rnA COMPLEMENTARY TRACKING
VOLTAGE REGULATOR
v"' __---~o-'-1
ORDERING INFORMATION
DEVICE
TEMPERATURE RANGE
MC1463R
OOC to+700C
229
Metal Power
Metal Can
MC1563G
MC1563R
PACKAGE
Metal Can
MC1463G
-55 0 Cto+1250C
Metal Power
MC1463, MC1563
MAXIMUM RATINGS (TC; +25 0 C unless otherwise noted.)
Symbol
Rating
Input Voltage
MC1463
MC1563
Unit
Value
Vdc
VI
-35
-40
G Package
R Package
load Current - Peak
IL
250
600
mA
Current. Pi n 2
12
10
10
mA
Po
I/R8JA
R8JA
Po
1/R8JC
R8JC
0.66
5.44
184
1.8
14.4
69.4
2.4
16
62
9.0
61
17
Watts
mW/oC
°C/W
Watts
mW/oC
°C/W
Power Dissipation and Thermal Characteristics
TA = 25°C
Derate above T A = 25°C
Thermal Resistance. Junction to Air
TC = 25°C
Derate above T C = 25° C
Thermal Resistance, Junction to Case
Operating and Storage Junction Temperature
Range
-65 to +150
T J. T stg
°c
OPERATING TEMPERATURE RANGE
Operating Ambient Temperature Range
MC1463
MC1563
ELECTRICAL CHARACTERISTICS
(I L ; 100 mAde. TC; +25 0 C. Vin ; 15 V. Vo ; 10 V unless otherwise noted.)
MC1463
MC1563
Fig. Note
Characteristic
Symbol
Min
Typ
Max
Unit
-
-35
Vdc
-
-32
Vdc
-3.5
-3.8
Vdc
1.5
3.0
Vdc
-
7.0
14
mAdc
-
-
120
-
,.,V(rmsl
-
-
Typ
Max
Min
-
-40
-9.0
4
1.6
VI
-8.5
Output Voltage Range (IL = 1.0 mAl
4
-3.6
-
-37
-3.8
4
-
Vo
Reference Voltage (Pin 1 to Groundl
Vref
-3.4
-3.5
-3.6
-3.2
Minimum Input·Output Voltage Differential
(R sc = 01
4
2
IVin' VOl
-
1.5
2.7
-
Bias Current (Standby Currontl
(lL = 1.0mAdc.IIB = II -ILl
4
-
liB
-
7.0
11
Output Noise
(C n = 0.1 ,.,F. f = 10 Hz to 5.0 MHzl
4
-
vN
-
120
-
Input Voltage
(T A = Tlow (]) to Thigh
I2i
IL = 1.0 mAl
Temperature Coefficient of Output Voltage
4
3
llVO/llT
Operating Load Current Range
(R se = 0.3 ohml R Package
(Rsc = 2.0 ohmsl G Package
4
-
ILR
Input Regulation (V in = 1.0 Vrms. f = 1.0 kHzl
4
4
Regline
Load Regulation
(T J = Constant [1.0 mA';;1 L .;; 20 mAli
(TC = +250 C [1.0 mA';;I L ';;50 mAli R Package
G Package
6
5
Regload
Output Impedance (f = 1.0 kHz)
7
-
zo
Shutdown Current
(V I = -35 Vdc)
8
-
Isd
+10/1 F
RL
13k
MC1563
MC1463
Va" -10 Vdc
FIGURE 8 - SHUTDOWN CURRENT
GND
'6k
R - IVin(m for ,-I---....L--..L.,
1 mAde
I
6"
10k
RL
RA
.'"
000I/1F
VI
~
-35 Vdc
10iJF
'0
10
231
MC1463, MC1563
GENERAL DESIGN INFORMATION
FIGURE 9 - TYPICAL CIRCUIT CONNECTION
1. Output Voltage. Vo
aJ Output Voltage is set by resistors RA and RB (see Figure 91.
Set RB = 6.8 k ohms and determine RA from the graph of
~'---------~--~-4~----~----~--~GNO
Figure 11 or from the equation:
Co
RA "" (2!VO!-7J kf!
01,uF
68 k
Rs
CASEI10
bl Output voltage can be varied by making RA adjustable as
shown in Figures 9 and 10.
cJ Output voltage. VO. IS determined by the ratio of RA and RB
therefore optimum temperature performance can be achieved
If RA and RS have the same temperature coeffiCient.
dJ Vo = Vrof (1 + RM; therefore the tolerance on
RB
output voltage is determined by the tolerance of Vref and
RA and RB·
2. Short-Circuit Current. ISC
Short-Circuit Current. ISC is determined by Rsc· Rsc may
be chosen with the aid of Figure 11 when using the typical
Select RA to Give DeSired
Va
circuit connection of Figure 9.
3. Compensation. Cc
A 0.001 I'F capacitor (C c • see Figure 9). will provide
FIGURE 10 - RA versus Vo
adequate compensation in most applications, with or without
60
current boost. Smaller values of Cc will reduce stability and
larger
value~
(RJ
of Cc will degrade pulse response and output
impedance versus frequency. The physical location of C c
should be close to the MC1563/MCI463 with short lead
lengths.
4. Noise Filter Capacitor. C n
A 0.1 I'F capacitor. Cn • from Pin 3 to ground will typically
reduce the output noise voltage to 120I'V(rms). The value
of C n can be increased or decreased, depending on the noise
voltage requirements of a particular apphcation. A minimum
value of 0.001 I'F is recommended.
~
w
z
«
t;;
~
j
V
V
40
V
30
V
20
V
10
//
o
o
-15
-10
-50
-20
-30
-25
-35
VO. OUTPUT VOL TAGE (VOL TSI
FIGURE 11 - Isc versus Rsc
500
:.t
IT
TJ
.E
I-
~
400
c
300
B
«
g
I-
7. Remote SenSing
The connection to Pin 8 can be made with a separate lead
direct to the load. Thus, "remote sensing" can be achieved
and the effect of undesired impedances (including that of
the milliammeter used to measure I L) on Zo can be greatlv
reduced.
~ 6 8 kSll_
'-'
5. Output Capacitor. Co
The value of Co should be at least 10 #F in order to provide
good stability.
6. ShutdOwn Control
One method of turning"OFF" the regulator is to draw 1 mA
from Pin 2 (See Figure 8). This control can be used to
eliminate power consumption by circuit loads which can be
put in "standby" mode. Examples include, an ac or dc
"squelch" control for communications circuits, and a disSipation control to protect the relJ.llator under sustained output short-circuiting. As the magnitude of the input-threshold
voltage at Pin 2 depends directly upon the junction temperature of the integrated circuit chip, a fixed dc voltage at Pin 2
will cause automatic shutdown for high junction temperatures. This will protect the chip. independent of the heat
sinking used, thl;! ambient temperature, ar the input or output voltage levels. Standard Logic levels of MRTL. MDTL'
ar MTTL * can also be used to turn the regulatar "ON" ar
"OFF".
~ (2 Vo .\) k!1)
50 f - - - (RB
'5 200
~
c::;
Ii;
c
~
~
100
\
\
" ---
=
I+25
0
C
"'-
10
I--
20
30
40
Rsc. EXTERNAL CURRENT·LlMITING RESISTOR (OHMS)
232
50
MC1463, MC1563
TYPICAL CHARACTERISTICS
Cn ; 0.1 /.1F, Cc ; 0.001 /.1F, Co; 10/.1F, TC; +25 0 C,
Unless otherwise noted:
VI(nom); -15 Vdc, VO(nom); -10 Vdc, IL; 100 mAdc.
FIGURE 12 - TEMPERATURE DEPENDENCE
OF SHORT-CIRCUIT LOAD CURRENT
FIGURE 13 - FREQUENCY DEPENDENCE
OF OUTPUT IMPEDANCE
1000
SOD
:<
.5
....
z
w
600
u
'"'"=>
500
c
~
....
~
i
700
Rsc
3n
400
4<2
300
5<2
100
Ion
13<2
~ 100
-75
:=
1000
2n
""""
-......
~
.......
--- -----------50
:::--
..................
+15
-15
500
/
~ 300
r-~
+50
----
~
V
200
~
r--
....
~ 100
S
o
j
50
/
30
+75
+100
+115
10
1.0
+150 +175
10
100
TJ. JUNCTION TEMPERATURE lOCI
FIGURE 14 - DEPENDENCE OF OUTPUT
IMPEDANCE ON OUTPUT VOLTAGE
FIGURE 15 - OUTPUT IMPEDANCE versus Rsc
40
50
5
c:
.5
J,
z
15
~
,.
10
....
2C
....
15
j
10
+1~OC
IVI- viOl- 3.0 TJ Rsc:= 0, I L := 10 rnA to 500 rnA
f - 1.0 kHz
30
w
'-'
....
:0
""'\
S
~ 0.98
-f---::: r:--.-K --
1". __
:g
~~
--
~
'"
.5
f-
~
-
5.0
~
~
~
a;
~
TJ '" +25 0 C
~
1.8
f---:::
L
V./
f..--"
-
I---':
TJ :+125 0 C
-10
-5.0
-20
-15
-25
-30
-35
o
-40
~
f
=
~II
1 kHz
;;- 0.006
o
>=
0.004
~
0.00 2
~
TJ"'+125OC
f-
~
TJ ° 550C ....::;:
r-- r-L
5.0
10
20
--=r==
-9 998
t--t---t----j----j----t----t---t---t---t---i
~
-10 000
i-i-t"-t--i--t--t---t::::::j::::::i==j
.
25
~ -1O.0061--t--i----t---j----t---t---t---t---t----i
I
,;' -10 008 ~_-'-_-"-_
35
30
__'__
_'__
+100
+100
04
=~
~
+25
"'
500"i\--
tPHl "tPlH '" 20 ns
-9.750
0.3
~ 02
+B5
~
"
~
f-
=>
-10.000
~
f-
=>
0
6
-10 250
10000
I
_I.
b
,;
L
G PtYGi
~
01
~
0 07
GO 05
---BONDING WIRE LIMITATIONS
-
00 1
30
10 ms/D1V
,
"
-'
_.J
,
=
=
~
I
- -THERMAL LIMITATIONS
f--Tc
10.002
>
MC1463R
MC1563R
"-
'" a 03
:3
- 00 2
\
_ _ '_
- - - - - SECONDARY BREAKDOWN LIMITATIONS
o
0
>
,
+90
9.99B
Ii
__'__
~jPACKAGE
+95
-=
-
0
~
w
+ d t L H ° (PHIL °
_ ' __
FIGURE 22 - DC OPERATING AREA
06
+50
_ L_
100 .us/D1V
+105
+75
__L._
40
+125
~
r=
II "50 rnA
FIGURE 21 - LOAD TRANSIENT RESPONSE
~w
500
400
300
Lttftll U
IVI - VOl, INPUT·OUTPUT VOLTAGE DIFFERENTIAL (VOLTS)
0""
I
u;
~
~
~-10004
VO--3.6V
15
200
>
r---::::::: k::::!
VO--10V-...
"'f-
Tco+125 0C -
~ -10.0021--+--+---t7-+-+-+--+---+--t--~
TJ '" +25 OC
0
Cl ]"
l'--
FIGURE 20 - INPUT TRANSIENT RESPONSE
0.008
!
:::::e::::
IL, LOAD CURRENT (mAdel
FIGURE 19 - EFFECT OF INPUT-OUTPUT VOLTAGE
DIFFERENTIAL ON INPUT REGULATION
~
...........
I
100
Vi", INPUT VO LTAGE (Vde)
Z
"'
"'/~
f---<
V
,/
1.0
o
~
~ '/
'\,1
TC ° +250C
4.0
:5=>
~V
Tco-55 0C
+
1
40
I
25 0 C
I
I
5.0
70
I
I
10
20
MC1463G
MC1163G
30
40
IVI- VO', INPUT·OUTPUT VOLTAGE DIFFERENTIAL (VOLTSI
234
50
®
MC1466L
MC1566L
MOTOROI.A
Specifications and Applications InforIllation
MONOLITHIC VOLTAGE AND
CURRENT REGULATOR
This unique "floating" regulator can deliver hundreds of volts limited only by the breakdown voltage of the external series pass transistor. Output voltage and output current are adjustable_ The MC1466/
MC1566 integra::d circuit voltage and current regulator is designed to
give "laboratory power-supply performance_
•
•
•
•
•
EPITAXIAL PASSIVATED
INTEGRATED CIRCUIT
Voltage/Current Regulation with Automatic Crossover
CERAMIC PACKAGE
Excellent Line Voltage Regulation, 0_01% +1.0 mV
CASE 632
TO-116
Excellent Load Voltage Regulation, 0.01% +1.0 mV
Short-Circuit Protection
Output Voltage Adjustable to Zero Volts
•
Adjustable I nternal Current Source
-
14
Excellent Current Regulation, 0.1% +1.0 mA
•
•
PRECISION WIDE-RANGE
VOLTAGE and
CURRENT REGULATOR
1
t!
I
i
•
I :
I
,
ORDERING INFORMATION
Internal Reference Voltage
Device
MC1466L
MC1566L
j
I
Temperature Range
oOc
to + 700 C
-55°C to+1250C
11
Package
Ceram,c DIP
Ceramic DIP
TYPICAL APPLICATiONS
FIGURE 1 - O-TO-15 VOC, lO-AMPERES REGULATOR
+
'
FIGURE 2 - O-TO-40 VDC, O_5-AMPERE REGULATOR
20 VOl
lN41}01
OR fOUIV
FIGURE 3 - O-TO-250 VDC, O_l-AMPERE REGULATOR
FIGURE 4 - REMOTE PROGRAMMING
lMOO!"! OR EOIJIV
CRS
v~o~o FORVp<20Vdc, R 0)
Pins 1,2,3,ilnd4 noconnect,on
235
RS
MC1466l, MC1566l
MAXIMUM RATINGS (TA = +25 0 unless otherwise noted)
Value
Symbol
Rating
Auxiliary Voltage
Unit
Vde
Vaux
30
35
MC1466
MC1566
Power Dissipation (Package Limitation)
Operating Temperature Range
mW
mW/oC
750
6.0
PD
1/0JA
Derate above T A = +50o C
JC
TA
a to
+70
-55 to +125
MC1466
MC1566
Storage Temperature Range
°c
-65 to +150
T stg
ELECTRICAL CHARACTERISTICS (TA = +25 0 C, Vaux = +25 Vdc unless otherwise noted)
Characteristic Definition
Symbol
Characteristic
Auxiliary Voltage (See Notes 1 & 2)
IVoltage from pin 14 to pin 71
Typ
Max
30
35
mAde
raux
9.0
MC1466
MC1566
7.0
12
8.5
18.2
18.2
19.7
19
1.0
10
1.2
1.1
6.0
3.0
12
6.0
Vde
I nternal Reference Voltage
IVoltage from pin 12 to pin 71
17.3
MC1466
MC1566
Reference Current (See Note 3)
17.5
'ref
MC1466
MC1566
Input Current-Pin 8
mAde
0.8
0.9
18
MC1466
MC1566
mW
Power DiSSipation
360
MC1466
MC1566
300
Input Offset Voltage, Voltage Control
Amplif,er ISee Note 41
a
MC1466
MC1566
Load Voltage Regulation
3.0
MC1466
MC1566
Line Voltage Regulation
ISee Note 61
mVdc
15
15
40
25
1.0
0.7
3.0
0.015
0.004
0.03
1.0
0.7
3.0
0.015
0.004
0.03
.6.Viov
MC1466
MC1566
ISee Note 51
Units
Vde
21
20
MC1466
MC1566
Auxiliary Current
Min
Vaux
!;VrefIVref
-
mV
1.0
%
0,01
aViov
MC1466
MC1566
MC1466 !;VrefIVref
MC1566
mV
1.0
%
0,01
Temperature Coefficient of Output Voltage
ITA = a to +75 0 CI
ITA = -55 to +25 0 CI
ITA = +25 to +125 0 CI
0.01
0.006
0.004
MC1466
MC1566
MC1566
I nput Offset Voltage, Current Control
Amplifier ISee Note 4)
(Voltage from pin 10 to pin 11)
a
MC1466
MC1566
3.0
mVde
15
15
40
25
Load Current Regulation
MC1466
MC1566
ISee Note 71
MC1466
MC1566
Ins
ana
q
no connec Ion.
236
!;I,ef
0.2
0.1
%
1.0
1.0
mAde
MC1466L, MC1566L
Load Voltage Regulation 0
NOTE 1:
The instantaneous Input voltage, V aux . must not exceed
the maximum value 01 30 volts lor the MC1466 or 35
volts for the
Me 1566.
l>Vrel (100"1<)
+ ll>V'
O
av
V
reI
The instantaneous value of Vaux
NOTE 6:
must be greater than 20 volts lor the MC 1566 or 21
Line Voltage Regulation is a function of the same two
additive components as Load Voltage Regulation, .6. V IOV
and .6. V ref (see note 51. The measurement procedure is
volts for the MC1466 for proper internal regulation.
NOTE 2:
The auxiliary supply voltage Vaux , must "float" and be
electrically Isolated from the unregulated high voltage
supply, Vin.
NOTE 3:
Set the auxiliary voltage, V aux . to 22 volts for
the MC 1566 or the MC 1466. Read the value of
b.
Change the Vaux to 28 volts for the MC1566 or
the MC1466 and note the value of Viov (2) and
V re f(2)' Then compute Line Voltage Regulation:
Viov (1) and Vrel (1).
Reference current may be set to any value of current
less than 1.2 mAde-by applying the relationship:
Irel (mA)
a.
0
8.55
Rl (km
l>V,ov l>Viov (11 - Viov (21
% Reference Regulation =
0
NOTE 4:
A built·in offset voltage (15 mVdc nominal) is provided
[Vrel (11 - Vrel (21J (100%1
Vrel (11
50 that the power supply output voltage or current may
be adjusted to zero
NOTE 5:
(100%)
Vrel
AVrel
- - (100%1 + AViov'
Load Voltage'Regulation is a function of two additive
components, .6.Viov and 6'vref, where AViov is the
change in input offset voltage (measured between pins 8
and 91 and b. V ref is the change in voltage across R2
(measured between pin 8 and ground). Each component
may be measured separately or the sum may be
measured across the load. The measurement procedure
for the test circuit shown is'
Vref
NOTE 7:
Load Current Regulation is measured by the following
procedure:
a. With 52 open, adjust R3 for an initial load current,
I L( 11, such that Vo is 8.0 Vdc.
b. With 52 closed, adjust RT lor Vo 0 1.0 Vdc and read
I L(2). Then Load Current Regulation 0
a. With 51 open (14 0 0) measure the value 01 Viov (11
and Vrel (11
b. Close 51, adjust R4 so that 140500 /.LA and note
V,ov (2) and Vrel (21·
Then b.viov 0 Viov (11 - Viov (21
% Reference Regulation
= l>Vrel
Line Voltage Regulation =
[1L(2) - IL(lI]
lUll
(100%1 + Irel
where Iref is 1.0 mAdc, Load Current Regulation is
specified In this manner because Iref passes through
the load In a direction opposite that of load current
and does not pass through the current sense resistor. Rs.
=
[V re l(11- V reI12IJ
,_l>Vrel
v re l(lI
(100Y,I- Vrel (100%1
FIGURE 5
BLOCK DIAGRAM
14
OUTPUT
INTERNAL
COMPENSATION
10
8
VOLTAGE
SENSE INPUT
CURRENT
SENSE INPUT
CIACUIT SCHEMATIC
196k
801
431
151
725V
221
INTERNAL
VOLTAGE
REGULATOR
REFERENCE
CURRENT
SOURCE
VOLTAGE
CONTROL
AMPLIfiER
237
CURRENT
CONTROL
AMPLIfiER
.R
OUTPUT
AMPLIFIER
®
MCI468
MCIS68
MOTOROLA
DUAL ±15-VOL T
TRACKING REGULATOR
DUAL ± 15-VOLT REGULATOR
The MC1568/MC1468 isadual polarity tracking regulator designed
to provide balanced positive and negative output voltages at currents
to 100 mAo Internally. the device is set for ± 15·volt outputs but an
external adjustment can be used to change both outputs simul·
taneously from 8.0 to 20 volts. Input voltages up to ± 30 volts can
be used and there is provision for adjustable current limiting. The
device is available in three package types to accomodate various
power requirements.
•
SILICON MONOLITHIC
INTEGRATED CIRCUIT
~
o
o0
10
o .. o~
o 1~1
Internally set to.± 15 V Tracking Outputs
• Output Currents to 100 mA
• Outputs Balanced to within 1% (MC1568)
(bottom view)
CASE SOOC
METAL PACKAGE
• Line and Load Regulation of 0.06%
• 1% Maximum Output Variation due to Temperature Changes
• Standby Current Drain of 3.0 mA
TO·IOO
G SUFFIX
• Externally Adjustable Current Limit
• Remote Sensing Provisions
• Case is at Ground Potential (R suffix package)
(bottom view)
CIRCUIT SCHEMATIC
CASE 614
METAL PACKAGE
R SUFFIX
Vee
4(7)
3(5)
,-------------oVo'
--==+++==~~;::::;_----r:-~SENSE
(t)
r
2(4)
CASE 632
CERAMIC PACKAGE
TO·116
L SUFFIX
COMPEN (.)
(2JSAlANCE
ADJUST
(lpackayeonlvl
11~3J~t--~-~--~
14
]----+-:--o
1I11l
r"""....--o SENSE (
(top view)
)
61101
+---.......oVo·
ORDERING INFORMATION
5un
GNO
1001
VOLTAGE
ADJUST
9114)
PIn numbers adtilcent to urmillais alP lor the G
anrl R SUI/IX paCkages mlly Pill numbers III lIa
lentheses are 1111 Ihe l suffl~ packa!Jl! only
DEVICE
COMPEN( I
MC1468G
8(12)
Pin 101$ ground 101 Ihe G 5ufhx package only
FOlllleRpackage.lheuselsground
MC1468L
MCI468R
MC1568G
MC1568L
MC156BA
238
TEMPERATURE RANGE
00 C to +70o C
0° C to +70 0 C
0° C to HOoC
-55° C to +125° C
_55° C to +125° C
-550 C to +125° C
PACKAGE
Metal Can
CeramiC DIP
Metal Power
Metal Can
CeramiC DIP
Metal Power
MC1468, MC1568
MAXIMUM RATINGS (TC = +25 0 C unless otherwise noted.1
Value
Symbol
Aating
I nput Voltage
Unit
Vdc
vcc,lveel
30
Peak Load Current
TA
= +25 0 C
G Package
A Package
l Package
0.8
2.4
28.5
35
9.0
61
17
1.0
10
PD
1/0JA
eJA
PD
l/eJC
e JC
Derate above T A = +25 0 C
Thermal Resistance, Junction to Air
TC = +25 0 C
Derate above T C = +25 0 C
Thermal Resistance, Junction to Case
6.6
150
2.1
14
70
Watts
mW/oC
100
°C/W
2.5
20
mW/oC
50
°C/W
Watts
TJ,Tstg
-65 to +175
°c
RSC(minl
4.0
Ohms
Storage Junction Temperature Range
MinimuITI Short-Circuit Resistance
mA
100
IpK
Power Dissipation and Thermal Characteristics
OPERATING TEMPERATURE RANGE
Ambient Temperature
o
to + 70
-55 to +125
MC1468
MC1568
= C4 = 1.0 ~F, RSC+
IL+:::: IL-::: 0 TC - +25 0 C unless otherwise noted) (S p 8 Figure 1)
ELECTRICAL CHARACTERISTICS (VCC = +20 V, Vee = -20 V, Cl = C2 = 1500 pF, C3
-
= RSC- = 4.0 n,
MC1468
MC1568
Symbol*
Min
Typ
Max
Min
Typ
Max
Unit
Output Voltage
Vo
+14.8
+15
+15.2
±14.5
+15
+15.5
Vdc
Input Voltage
Vin
-
-
±30
-
-
±30
Vdc
IVin-VOI
2.0
-
-
2.0
-
-
Vdc
Output Voltage Balance
VBal
-
±50
±300
mV
Line Regulation Voltage
(Vin = 18 V to 30 VI
Regin
Characteristic
Input-Output Voltage Differential
= Tlow
-
-
to Thigh)
= 120 Hzl
Short-Circuit Current Limit
IB
Negative Standby Current
18
Tlow = OOC for MC 1468
= -55°C for MC1568
10
30
-
-
10
30
-
±20
±20
±8.0
+14.5
-
±20
+20
-
75
-
-
75
-
-
0.3
1.0
-
0.3
1.0
-
60
-
-
60
-
-
100
-
-
100
-
-
2.4
4.0
-
2.4
4.0
-
1.0
3.0
-
1.0
3.0
6VO/6t
-
0.2
-
-
0.2
-
Q)
dB
%
mA
~V(RMSI
mA
-
VI
long-Term Stability
-1 VEE
MCt568R
MC1468R
ISC ~RSC
R2
(+)
MC1568l
VO·
INPUT (-)
••'5k
SENSE (-I
CQMPEN ( )
VO-
VEE
SENSE ( I
10
RSC-
11
'--"N\-+-----------<>-_.-VO
The presence oj the Saladl_ pin 2, on deVices
housed In the dual If! ilnepiI[kagell sulfl~) allows
the user to adjust the output voltages down to
.80 V The leQlIIfed value of re~stor A2 can
calculated from
j---+-JVv'V-+---------<>-__ -15 Vnc
tN3055
OR EQUIV
033.\1
20W
-Va
Al Rlt'll (0+ VI)
R2~ RmdVO ,)-V I )-oRl
Where R It'll
~
At'llrltemal ReSistor
~
OS8V
SSV
Q
VI
240
=
R 1 ~ 1 kit
Some common design values are listed below
.vo,V) A2
14
12
12k
18k
10
35k
80
Te
Vo
(%/oc)
18 + (rnA)
0003
10
0022
0025
"
0028
50
26
MC1468, MC1568
TYPICAL CHARACTERISTICS
Vo = ± 15 V, T A = +25 0 C unless otherwise noted.)
= +20 V, VEE = -20 V,
(Vcc
FIGURE 6 - REGULATOR DROPOUT VOLTAGE
FIGURE 5 - LOAD REGULATION
..'"
40
w
:;
.5
z
.
0
>=
.
w
1.0
1--
2.0
::?-
=>~
0.1I-~
l=>
0
POSITIJE
r
0."
~i=
3.0
2.0
,,~
=>'"
~~
--
~ >--
I--- I--
z~
:Eo
RSC" 4 0 OHMS
TJ" TA
5.0
1.0
:>
40
o
o
60
FIGURE 7 - MAXIMUM CURRENT CAPABILITY
'\. '\
'\
16 o " - - v "
VCC" I VEE I
" ;"
'\.
- - - - NO HEATSINK
INFINITE HEATSINK
---
~
'
I
:...\
I
80
I-
o
I-
R PACKAGE 0
r--
-"
!----
\
.:::
.
~
~
+75
+ 100
....... ............
80
~
o
o
+125
i'-.
" r--..
0
8.0
- r--
S
I\.
4.0
-
..
\
\
I-
\ I
MC 156B)
25
-55
.5
A --\r\
L PACKAGE ....
\
f-I---; f--
>
60
7.0
.5
--
REG~LATO~,
=>~
>::; 4.0
0
>
~
3.0
=>0
'"
I-
O~MS
6V01" 100
>
0
~
0
I
I - - I- RSC " 4.0
>::;
12
16
-20
24
~
>=
"
i-.
40
RSC
200HMS
+25
+50
~
28
0
o
32
-75
-50
-15
+75
TJ. JUNCTION TEMPERATURE lOCI
RSC. SHORT·CIRCUIT RESISTOR (OHMS)
241
+100
+125
MC1468, MC1568
TYPICAL CHARACTERISTICS (continued)
(VCC = +20 V. VEE = -20 V. Vo =±15 V. TA = +25 0 C unless otherwise noted.)
FIGURE 11 - STANDBY CURRENT DRAIN
FIGURE 12 - STANDBY CURRENT DRAIN
0
5.0
I
9, 0
I--VCCo IVEEI
:<
8, 0
4.0
:<
.5
~
3.0
....-:;
'"
,...i3
~
2.0
0/
POSITIVE STANDBY CURRENT
"
4. 0
~
z 3.0
.,;
.'E
55°C
+25 0 C
18
16
22
20
24
26
28
30
--
f----
2, 0
+125 0 C
/'
I-~i;:6~~ECU RRENT~
o
0
0
15
32
16
17
6
I
I
,I
VCC ° VEE ° 30 V
Rsc ° 4.0 OHMS
1
c;
~
I--- THERMAL SHIFT -
I
1,
I
1\
E
-
-
-
;;
f--- +--
l--- ~
l--- ~
0
20
FIGURE 14 - LOAD TRANSIENT RESPONSE
I
3
~ 0.0 2
19
>
I
00 4
18
±VO, OUTPUT VOLTAGE (±V)
FIGURE 13 - TEMPERATURE COEFFICIENT OF
OUTPUT VOLTAGE
005i--
f...-
~EGATIVE STANDBY CURRENT
±V",INPUT VOLTAGE (±VI
0.0
....... I--
POSITIVE STANDBY C~Y
5, 0
'"u=>
,...
+125 0 C
0
6. 0
~
-55°C
+25 0 C
I
7. 0
.5
,...
f---
POSITIV'E REGULATOR
IL
61LoO-10mA
r - RSC ° 10 OHMS
NEGATIVE REGULATOR
% CHANGE IN Vo
CHANGE IN JUNCTION TEMPERATURE-
I
I
16
I
I
I
18
17
I
I
19
20
TIME,20"s/OIV
±VO. OUTPUT VOLTAGE (±V)
FIGURE 15 - LINE TRANSIENT RESPONSE
FIGURE 16 - RIPPLE REJECTION
0
.WCC 10 +20
J
10
-1 0
+23l
POSITIV'E
REG~LATO~
~
z
0
NEGATIVE
REGULATOR
-2 0
~ -4 0
_
6V 1n
:=
+20 to +23 V
I RSC ° 110 OHM1S
,...,...~
-5 0
'"
-6 P
w
[,vEE ° -20 V to -23V
7
/
NEGATIVE REGULATOR-
~
~
~
_.
'",...
~
"
TIME,50""OIV
~
RSC 0\0 OHMS
'L ° 10 mA
-3 0
>=
./'
/
L
-7 0
-8 0
-9 0
/
r-
-10 0
100
b--:-:" I-'
1.0 k
~
f-"'""
./
10k
f, INPUT FREQUENCY (Hz)
242
PO!ITIVE
REGULATOR
100 k
10M
@ MOTOROLA
MC1469
MC1569
Specifications and Applications InforIllation
MONOLITHIC VOLTAGE REGULATOR
POSITIVE VOLTAGE REGULATOR
INTEGRATED CIRCUIT
The MC1569/MC1469 is a positive voltage regulator designed to
deliver continuous load current up to 500 mAdc. Output voltage is
adjustable from 2.5 Vdc to 37 Vdc. The MC1569 is specified for
use within the military temperature range (-55 to +125 0 C) and the
MC1469 within the 0 to +700 C temperature range.
For systems requiring a positive regulated voltage, the MC1569
can be used with performance nearly identical to the MC 1563 negative
voltage regulator. Systems requiring both a positive and negative
regulated voltage can use the MC1569 and MC1563 as complementary
regulators with a common input ground.
• Electronic "Shut-Down" Control
•
Excellent Load Regulation (Low Output Impedance - 20 milliohms typ)
•
High Power Capability: up to 17.5 Watts
•
Excellent Temperature Stability: ±0.002 %/oC typ
SILICON NONOLITHIC
EPITAXIAL PASSIVATED
(Bottom View)
CASE 603
METAL PACKAGE
G SUFFIX
• High Ripple Rejection: 0.002 %/V typ
FIGURE 1- ±.15 V,±.400 mA COMPLEMENTARY TRACKING
VOLTAGE REGULATOR
..
~
+15Vdc
+20 Vdc
0- <·-0
3.
9
CASE 614
(bottom view)
METAL PACKAGE
R SUFFIX
3.
ORDERING INFORMATION
lOfJ F _
DEVICE
ro-4~----------~~---4--~VO
-15 Vdc
500 rnA max
FIGURE 2 - TYPICAL CIRCUIT CONNECTION
13.5 200 mA for R package only.
FIGURE 13 - DEPENDENCE OF OUTPUT
IMPEDANCE ON OUTPUT VOLTAGE
FIGURE 14 - OUTPUT IMPEDANCE versus Rsc
50,----,----,---,,---,----,---,----,---,
40r---.----.------,----,----.---,----,---.
u;
~ 40r---~----+_---+----1_--~----~--~r---~
o
30~--4---+----1----+---+----I-----+----1
j
~ 30r---~----+_---+----1_--~----~--~r---~
..,.....z
Rsc = 0
~ 20~--~~~~~=i~~~==~====~==~~--~
"!;
f-
~
~
o
10~--+--4--+_--+--t_-_+--~___1
10~--_t----+_---+----4_--_4----~--~~--~
j
OL-__
o
~
__
5.0
~
10
___ L_ _ _ _ _ _ _ _L __ _
35
15
25
30
20
~
~
~
__
~
40
lL=50mA
cr
:? 0.004
z
1
'"tB
~
10
1.0
01
100
II
Cf
§ 0.003
1 1
-r1
Cc=~.IMF
'"
~
f-
0.002
~
1
1
I I I
-
-",. i.-
0.001
II
Cc = 0.01 MF
Cc "O.I"F
II
1.0
1000
10
5. 0
1.01 ~-+---+--+--+--4_-4_-~-+-_t-_I
~
0.99~-~--1----1-_4---I---+--+-+-H---1
o
0.9Br--t---t---+-Rsc = 6.B ohms -+--~--+----1H---I
::i'
oS
f-
~
~
~
1--+--+--+--+-_4-_4---~-I--_tt-~
~ 0.95~-+---+---+--+--4_-4_-+-+-H_-_I
~00~~1:rr
20
40
so
I
i 19
BO
.-
4. 5
~
0.97 r--t----t---+--+_-1_-1_-~-+--t+-_1
~ 0.96
..-/ "/
TJ" t75 0C AND +125 OC
> 1.00~-~~-~-~--.j.--+--+-+",,",,+---i
~
/'"
1.02'f---+---+_-1_-+-~-~-_+-~--+----1
o
:il
N
1000
FIGURE 18 - BIAS CURRENT versus INPUT VOLTAGE
FIGURE 17 - CURRENT-LIMITING CHARACTERISTICS
~
100
f. FREQUENCY (kHz)
1.03 ,------,----,----,----,----,---,--,---,---,---,
'"~
"T"~
Cc = 0.001 MF
f. FREQUENCY (kHz)
w
16
IL=50mA
z
Cc 0.01 MF
1°·001
14
o
I I
f"::::
~
12
~
Cc = 0.001 MF
~ 0.002
10
I
g 0.004
1~"~
I II
o
~ 0.003
B.O
0.005
I II
~
6.0
FIGURE 16 - FREQUENCY DEPENDENCE
OF INPUT REGULATION, Co = 2.0 J.lF
FIGURE 15 - FREQUENCY DEPENDENCE
OF INPUT REGULATION, Co = 10 J.lF
0.005
4.0
2.0
Rsc, EXTERNAL CURRENT LIMITING RESISTOR (OHMS)
Va, OUTPUT VOLTAGE (VOLTSI
100
~V
\
1.---1- t:/:::: j:.XTJ"t250C /
~
TJ=OOC
..,'"
0;
I--
~
1----
IL" 1.0 mA
R2=S.Bk
---
4. 0
5.0
V
10
V
15
1/
7
\
20
Tp -55 0C - - - f----
i
-I
25
30
Vin, INPUT VOLTAGE (VOLTS)
IL,LOAO CURRENT (mA)
247
35
40
MC1469, MC1569
TYPICAL CHARACTERISTICS (continued)
Unless otheowise noted:
CN
= 0.1
Vin nom
IL
J.l.F, Cc = 0.001 J.l.F, Co = 1.0 J.I.F, T C = +25°C,
= +9.0 Vdc, Vo nom = +5.0 Vdc,
> 200 mA for R package on Iy.
FIGURE 20 - EFFECT OF INPUT-OUTPUT VOLTAGE
DIFFERENTIAL ON INPUT REGULATION
FIGURE 19 - EFFECT OF LOAD CURRENT ON
INPUT-OUTPUT VOLTAGE DIFFERENTIAL
2.5'~~~1~~--=~==_"----"
0.004
\..
2.41-------1t7"'~--_+---~*""""=~-_i
w
'0
>
'"
~ ~ 2.31----7''''-_t-----=--'"~'-----_t~_~~_i
«
~
§;
2.21-7~---_t__;;;,./-'----'rt-_:;>...,..=-_t----_1
i=
«
~:;
~
~ ~ 2.1 t----:7"'-t------:7"'~----+.----_1
.....
~
~
~ ~2.0
~ 0.00 1
6~
~
0.002
'"w
TC=+25 0 C
:::) UJ
"-
~
>~
~
0.003
I
1.91----7"'---+-
0
'"""
TJ'" +125 0C
,L
........... t-....
""" i"b-
l"-
r--
-
TJ =+25 0 C
I
.-f - -
TJ '" -55°C
IL'" 1.0 rnA
'>
'-._-VO"3.5Vd,
-~~.-
ffi;10Vd'
8.0
500
Il. lOAD CURRENT (mAd,1
16
32
24
V;n . VO. INPUT·OUTPUT VOLTAGE DIFFERENTIAL (VOL TSI
FIGURE 22 - TEMPERATURE DEPENDENCE OF
SHORT-CIRCUIT LOAD CURRENT
FIGURE 21 - INPUT TRANSIENT RESPONSE
400
'"
.s>-
~=>
u
>
250
200
S
>-
~ ~ 1O.0021----j_--j_--lI'---+_C-',_"-+-0._1"_F-t-_-,t-_-+_-+_-t
Cc '" O.Ol,uF
1------j----j--4'--+-'--t--t-+-_t-_t-_1
10.000 i--j--\--'r--t--t--+---+--t---t---i
~ 9.9991-----1----j--f--t--+--+--+--+-+---j
9.998'-----'_--'_--'_--'_--1.._-'-_-'-_-'-_-'-_-'
~ ~ 10.001
300
"
10 003l===+===+=:::=::!===F==1==:=::.t===t==4==t:::::::-=1
a...
350
~
150
:;';
100
'"z
50
U
,g;;
0",
~
j
---- - --
Rsc'" 2.4 n
- r-
Rsc l-lOn
r--
I---
o
-75
1000
~
~ 800
CO"lO"FII
~
----
~
----
~ 400
~
~ 200
V
./
1000
1.0
~
II
+125
j
C, - O.Ol"F
~
~ 600
r-rn
cO" 2.0MF
o 800
CC '" 0.1 J.lF
II
~
........
Cc '" 0.1 pF
~
C," O.OOl"F
400
r-
C," O.Ol"F
~
C," 100i"t
V
~ 200
V
,., f-'"
,./
--r-
o
10
+100
III
v;
~
1/
+75
~ 3.3 n
FIGURE 24 - FREQUENCY DEPENDENCE
OF OUTPUT IMPEDANCE, Co = 2.0 J.l.F
II II
v;
;;;
+50
Rsc
TA. AMBIENT TEMPERATURE (OCI
FIGURE 23 - FREQUENCY DEPENDENCE
OF OUTPUT IMPEDANCE, Co = 10 J.l.F
~ 600
+25
-25
-50
100 MslOIV
w
r-- r-r-- r-- I---
100
1000
0.5
f, FREQUENCY (kHzl
1.0
5.0
10
50
f, FREQUENCY (kHzl
248
100
j
I
500
®
MC1723
MC1723C
MOTOROLA
VOLTAGE REGULATOR
MONOLITHIC VOLTAGE REGULATOR
SILICON
MONOLITHIC
INTEGRATED CIRCUIT
The MC1723 is a positive or negative voltage regulator designed
to deliver load current to 150 mAdc. Output current capability can
be increased to several amperes through use of one or more external
pass transistors. MC1723 is specified for operation over the military
temperature range (-55 0 C to + 125 0 C) and the MC 1723C over the
commercial temperature range (0 to +70 0 C)
• Output Voltage Adjustable from 2 Vdc to 37 Vdc
(top view)
• Output Current to 150 mAdc Without External Pass Transistors
• 0.01 % Line and 0.03% Load Regulation
14
P SUFFIX
PLASTIC PACKAGE
CASE 646
• Adjustable Short-Circuit Protection
FIGURE 1 - CIRCUIT SCHEMATIC
(top v;ew)
~o.
2 1
o
Vee
,-----,---t_----,-T---1r---~---t_--'c:12.:.:I8~
Vc
G SUFFIX
71111
0
00
METAL PACKAGE
CASE 603
(TO-100 Type)
[:::::1
14
61V
L SUFFIX
CERAMIC PACKAGE
CASE 632
(TO-116)
ORDERING INFORMATION
Temperature
Range
Package
MC1723CG LM723CH,
~A723HC
oOc to JOce
Metal Can
MC1723CL
LM723CJ,
IJ-A723DC
MC1723CP
LM723CN, MA723PC
OoC to +70 o C
OoC to +70 o C
Device
NON-INVERTING
INPUT
INVERTING
INPUT
PIN NUMBERS ADJACENT TO TERMINALS ARE FOR THE METAL, PACKAGE
PIN NUMBERS IN PARENTHESIS ARE FOR DUAL IN LINE PACKAGES
Alternate
Ceramic DIP
MC1723G
-5SoC to +12SoC Metal Can
MCl723L
-5S0C to +12S 0 C
Ceramic DIP
FIGURE 3 - TYPICAL NPN CURRENT BOOST CONNECTION
FIGURE 2 - TYPICAL CIRCUIT CONNECTION
(7 < VO<37l
6 (101
Rse
R_SC'V°VlO~33...-. .
, - - - - - - - - - - : = 7 7 ( --:.--..
VO= +15 Vdc
'L '-2 Adcmax
MC1723
(MCl723C)
(5)3
I
12k
e,,,
(7)5
~ o~7(~~)
R2
10k
ISC
='
V~~n;1l
"
~
at TJ
=
+251lC
Fllrbest results 10k< R2< 100 k
For minimum drift R3 = Rl11R2
249
MC1723, MC1723C
MAXIMUM RATINGS (TA = +25 0C unless otherwise noted.)
Value
Symbol
Rating
Unit
Vin(p)
50
Vpeak
Vin
40
Vde
Vin - Vo
40
Vde
Maximum Output Current
IL
150
mAde
Current from Vref
Iref
15
mAde
Current from V z
Iz
25
Voltage Between Non·lnverting Input and Vee
Vie
8.0
Vde
Differential Input Voltage
Vid
±5.0
Vdc
Po
l/eJA
8JA
1.25
10
100
W
mW/oC
Po
l/eJA
8JA
Po
l/eJA
8JC
Po
1.0
6.6
150
2.1
14
35
1.5
10
100
Watt
Pulse Voltage from VCC to Vee (50 ms)
Continuous Voltage from VCC to Vee
Input·Output Voltage Differential
mA
Power Dissipation and Thermal Characteristics
Plastic Package
TA = +25 0C
Derate above T A = +25 0 C
Thermal Resistance, Junction to Air
Metal Package
TA = +25 0C
Derate above T A = +25 0 C
Thermal Resistance. Junction to Air
TC = +25 0 C
Derate above T A = +25 0 C
Thermal Resistance. Junction to Case
Dual In-Line Ceramic Package
Derate above T A = +25 0 C
Thermal Resistance, Junction to Air
1/8JA
8JA
Operating and Storage Junction Temperature Range
Metal Package
Dual In-Line Ceramic and Ceramic Flat Packages
°c/W
mW/oC
°C/W
Watts
mW/oC
°C/W
Watt
mW/oC
°O/W
TJ, Tstg
°c
-65 to +150
-65 to +175
Operating Ambient Temperature Range
DC
TA
o to +70
MC1723C
MC1723
-55 to +125
ELECTRICAL CHARACTERISTICS (Unless otherwise noted: TA = +25 0 C, Vin 12 Vdc, Vo = 5.0 Vdc, I L = 1.0 mAde, RSC = 0,
C1 = 100 pF, Cref = 0 and divider impedance as seen by the error amplifier
< 10 kn connected as shown in Figure
MCl723
2)
MC1723C
Symbol
Min
Typ
Max
Min
Typ
Max
Unit
I nput Voltage Range
Vin
9.5
-
40
9.5
-
40
Vdc
Output Voltage Range
Vo
2.0
-
37
2.0
-
37
Vdc
Vin-Va
3.0
-
38
3.0
-
38
Vdc
Reference Voltage
Vret
6.95
7.15
7.35
6.80
7.15
7.50
Vdc
Standby Current Drain (I L = 0, Vin = 30 V)
liB
VN
-
2.3
3.5
-
2.3
4.0
mAde
-
20
2.5
-
-
20
2.5
-
0.002
0.D15
-
0.003
0.D15
0.D1
0.02
0.1
0.2
-
0.D1
0.1
0.1
0.5
0.3
-
-
0.3
Characteristic
I nput-Output Voltage 0 ifferential
Output Noise Voltage (f - 100 Hz to 10 kHz)
Cref = 0
Cref = 5.0 /IF
Average Temperat(f) Coefficient of Output
Voltage (Tlow 1 Tlow
=
OOC for MC1723C
= _55°C for MC1723
%PC
%VO
-
(T
Load Regulation 11.0mA't
-
0.1
-
-
0.1
-
%/1000Hr
RejR
dB
@Thi9h = +70 0 C for MC1723C
= +125 0 C for MC1723
250
MC1123, MC1123C
TYPICAL CHARACTERISTICS
(Vin
= 12 Vde,
Va
= 5.0 Vde.
IL
= 1.0 mAde,
RSC
= O. T A = +25 0 C unless otherwise noted.)
FIGURE 4 - MAXIMUM LOAO CURRENT AS A FUNCTION
OF INPUT·OUTPUT VOLTAGE OIFFERENTIAL
FIGURE 5 - LOAO REGULATION CHARACTERISTICS
WITHOUT CURRENT LIMITING
200
+0.05
TJ max = 150 0 C
RTH = 1500CIW PSTAN OBY = 60 mW
;( 160
T-r~
E
>-
a:i
..
\
c
=:
~
\
=>
TA=+250C
~ -0.05
\J I
""-
'"'
-0.15
40
o
20
-
>
z
'"~ -0.0 5
f': I:::-
=>
r-- r-- r-
r--- ~ r...... t-.
T~=~
'"'
c
.. -0.2
T-h.
TA = +125 0C
RSC= Ion
015
9
~
!
o
r--
15
10
20
30
25
RSC =10n
o
'"
1.0
~
w
to
W
~
..............
'"
>
w
-
>-
::;
>-
TAi+250C
~
'"
~
0.2
'"'
TA=-550C
o
o
I
20
40
SEJSE
60
I"
\
1\
80
60
~
I'..
L
0.6
V
.L
'"
...........
1
::S:~
L1MITCURRENT RSC=5n
80
0.5
0.4
100
[l- r-- r-LIMIT CURRENT RSC = 10 n
-50
200
vat TAGE
;;;
TA=+1250C
0.4
>=
~
0.7
«
O.B
~
'"
~
~
in
~
>
40
20
0.8
RSC = 10 n
w
\
I
FIGURE 9 - CURRENT LIMITING CHARACTERISTICS
AS A FUNCTION OF JUNCTION TEMPERATURE
1.2
~
=>
TA =+25 0C\
10. OUTPUT CURRENT (mAl
FIGURE 8 - CURRENT LIMITING CHARACTERISTICS
'">>-
,
-~ ["-..,TA = -55°C
~~
TA = +125 0C,l
10. OUTPUT CURRENT (mAl
to
~
_\
-0.3
-0.4
5.0
"\
w
r-- ::i-=k
-0. 1
R" ~-......;
-0. 1
to
!'
..
~100
~ b-,
'"
~
=>
TA = -55°C
9
~
80
'0
>
.::z
~
.::
'"
~l~
60
40
-
+0.1
'0
-0.2
!:::::::,.
TA = -55°C
FIGURE 7 - LOAO REGULATION CHARACTERISTICS
WITH CURRENT LIMITING
+0.05
t
r--
0C
10. OUTPUT CURRENT (mAl
FIGURE 6 - LOAO REGULATION CHARACTERISTICS
WITH CURRENT LIMITING
~
~
............
Vin-Vo.INPUT·OUTPUT VOLTAGE (VOLTSI
~
TA - +25
I"'"-'- r::::::",.,
-0.1
30
20
10
i'-...
-
9
~A=+125~ I'-.....
J~
TA~tso;- r-- ~ t--
o
o
~ :-- t--.......:: r---. I""----,
«
'"
r.-. '\.f'...
40
~
z
'"
I\.
80
!"
~
\ 1\
120
''=>""''
u
'0
(No heat sink)
+50
""-:
~
r-- r-+100
TJ. JUNCTION TEMPERATURE (OCI
10. OUTPUT CURRENT (mAl
251
1
~
r---..
"':-:--".
40
+150
MC1723, MC1723C
TVPICAL CHARACTERISTICS (continued)
FIGURE 10 - LINE REGULATION AS A FUNCTION
OF INPUT-OUTPUT VOLTAGE OIFFERENTIAL
+0. 2
.1Vin
I
=
FIGURE 11 - LOAD REGULATION AS A FUNCTION
OF INPUT-OUTPUT VOLTAGE DIFFERENTIAL
+0. 1
+3 V
~
I =1
"0
"0
~
it'.
e +0. 1
l-
'"
::>
~w
---
~
Z
:::;
c
I
-0. 1
5.0
~
'"
«
l"-
g
-0. 1
...... f"
~
-0. 2
15
35
25
4.0
FIGURE 13 - LINE'TRANSIENT RESPONSE
I
2.0
i:;
'"z
.,--.....
1.0
.§
z
~
~
~
'"
+2.0 C
II
'"
~
z
'"
~
~
:;
o
~ +2. 0
_k-:-:-
to
TA =+25 0 C
~
~
'">
~
~
'-
~
::>
'"
40
30
to
«
OUTPUT VOLTAGE
I-
I-20
b..
lL
'">
I-
~
W
L
~
TA = +125 0 C
10
~
1
:;
TA = -55 0 C
---
~
+40
IN~UT VdLTAG'E
IL = 0
::'i
50
Vin -Va, INPUT·OUTPUT VOLTAGE (VOL TS)
f--- Va = Vret
«
to IL 150 rnA
z
z
'"'"::>
'-'
.,1
>
-2.0
-5.0
+10
+ 40 +45
+30
+20
Vin, INPUT VOLTAGE (VOLTS)
FIGURE 15 - OUTPUT IMPEDANCE AS
FUNCTION OF FREQUENCY
FIGURE 14 - LOAD TRANSIENT RESPONSE
+10
:;
1\
.§
z
'">=
~
~
'"~
~
../
1\
1\
'">
.§
z
V
'"w
I-
'"
-8.0
-5.0
\.
+10
10
IL =40 mA
LOAO CURRENT
+20
+30
+40
"''"S
:::ll=50mi>.:
CI"O
:>::
w
'-'
~
1.0
'"«
I
'"~
."F.
~
./
I-
::>
Q.
l-
::>
o. 1
'"~
0.0 1
100
+45
t, TIME",,)
1.0 k
10 k
t, FREQUENCY (Hz)
252
1
k
1M
MC1723, MC1723C
TYPICAL APPLICATIONS
Pin numbers adjacent to terminals are for the metal, package;
pin numbers in parenthesis are for the dual in-line packages.
< Vo < 7
FIGURE 16 - TYPICAL CONNECTION FOR 2
6(10)
FIGURE 17 - MC1723,C FOLDBACK CONNECTION
RSC
(11) 8
Va
RSC
6(10)
Va
+V.n
(11)7
RA
10 (1)
Rl
MCI713
(MC1713C)
MC1713
(MC1713C)
R3
(5) 3
100 pF
Rl
(7)5
1 (3)
5(7)
ISC '" Vsense
RSC
~
0.66 at TJ"' +250C
AA"'l~
RSC
For best results 10 k < Rl + R2 < 100 k.
For minimum drift R3 '" RlIIR2.
lOkS"!
where
[
Iknee
ISC
_11
J
A _ Vsense
SC - (1--0) ISC
FIGURE 19 - +5 V, 1-AMPERE HIGH
EFFICIENCY REGULATOR
FIGURE 18 - +5 V, 1-AMPERE SWITCHING REGULATOR,
Vin 1
=lmH
Va
+65V"'~----------------~~~;(
'T' O.I"F
IN4001
Vin 1
or EqUiv
+10 V
100
Vin
6(10)
(6) 4
MCI713
(MCI713C)
11k
J
10
+5V
10(1)
MC1713
(MC1713C)
1k
(5) 3
1 (4)
(5)3
5.1k
(11) 8
-
1(3)
1M
Ik
01"F
-::!,-
Va
(11) 8
+10V
0.33
:r
9(13)
51k
5(7)
(7) 5
FIGURE 20 - +15 V, 1-AMPERE REGULATOR
WITH REMOTE SENSE
033
FIGURE 21 - -'5 V NEGATIVE REGULATOR
6 (10)
Vin
(11) 8
tl0 V ........---<~-<>-I
2 (4)
(6) 4
11k
+ Sense
MC1713
(MC1713C)
Va
+15
10 k
1000 pF
~-
v
Load
-Sense
-=
253
Vm =-20V
+5 V
®
MC3420
MC3520
MOTOROLA
SWITCHMODE REGULATOR CONTROL CIRCUIT
The MC3520/3420 is an inverter control unit which provides all
the control circuitry for PWM push-pull, bridge and series type
switch mode power supplies.
These devices are designed to supply the pulse width modulated
drive to the base of two external power transistors. Other applications where these devices can be used are in transformerless voltage
doublers, transformer coupled dc-to-dc converters and other power
control functions.
The MC3520 is specified over the military operating range of
-55 0 C to +125 0 C. The MC3420 is specified from OOC to +70 0 C.
•
Includes Symmetrical Oscillator
•
On Chip Pulse Width Modulator, Voltage Reference,
Dead Time Comparator, and Phase Splitter
SWITCHMODE REGULATOR
CONTROL CIRCUIT
SILICON MONOLITHIC
INTEGRATED CIRCUITS
P SUFFIX
PLASTIC PACKAGE
CASE 648
• Output Frequency Adjustable (2 kHz to 100 kHzl
•
Inhibit and Symmetry Correction I nputs Available
• Controlled Start-Up
•
•
L SUFFIX
Frequency and Dead Time are I ndependently Adjustable
(0% to 100%1
CERAMIC PACKAGE
CASE 620
Can be Slaved to Other MC3420s
• Open Collector Outputs
•
Output Capability 50 mA (Max.1
Output 2
PIN CONNECTIONS
Inhibit!
Symmetry
Correction
• On Chip Protection Against Double Pulsing of Same Output
During Load Transient Condition
Input
Inhibit
Osc.
Output
Output 2
FIGURE 1-TYPICAL APPLICATION
Ground
Output 1
Dead Time
Adjust
+10to3QV
Vee
10 k
:1~;U~h~:
11
} ~Oase
Drive
,I Current
,-I
Delay
I
I
Circuit I
I_ _ _ _ _ _ J
Circuit
I
ORDERING INFORMATION
VA
to V sense
254
DEVICE
TEMPERATURE
RANGE
PACKAGE
MC3420P
Oto+70°C
Plastic DIP
MC3420L
o to +70"'C
Ceramic OIP
MC3520L
-55 to +12S o C
Ceramic DIP
MC3420, MC3520
MAXIMUM RATINGS
Rating
MC3420
MC3520
Symbol
Unit
Power Supply Voltage
VCC
30
Output Voltage (pins 11 and 13)
V out
40
V
Oscillator Output Voltage (pin 14)
V14
30
V
Voltage at pin 4
Voltage at pins 3 and 8
V
V4
2.0
V
V3, V8
5.0
V
V
Voltage at pin 5
V5
7.0
Power Dissipation
Po
See Thermal Information
Operating Junction Temperature
TJ
150
125
150
-55 to +125
o to +70
Ceramic Package
Operating Ambient Temperature Range
TA
Storage Temperature Range
°c
-
Plastic Package
T 5t9
-65 to +150 -65 to +150
°c
°c
Characteri.$tic
REFERENCE SECTION
Reference Voltage
5
Vref
7.6
7.8
8.0
7.4
7.8
8.2
V
5
TCVref
-
0.008
0.03
-
0.008
0.03
%/oC
5
Reg(in)
-
3.0
5.0
7.5
-
7.5
-
-
4.0
5.0
IIref = 400 "A)
Temperature Coefficient of Reference Voltage
(VCC = 15 V, Iref = 400 pAl
Input Regulation of Reference Voltage
lire! = 400 "A)
IIref = 1.0 mAl
DC SUPPLY SECTION
mVtv
-
Supply Voltage
5
Vin
10
-
30
10
V
5
10
-
-
16
-
-
30
Supply Current
22
mA
At
At
-
-
3.0
%
-
-
0.03
-
5.0
-
0.04
%/oC
(R ext
=
10 kil, excluding load and current and
reference current)
OSCILLATOR SECTION
Line Frequency Stability
(f = 20 kHz)
(t = 20 kHz, VCC = 15 V, Tlow to Thigh)
5
Maximum Output Frequency
6
f max
100
200
-
100
200
-
6
fmin
-
2.0
5.0
-
2.0
5.0
kHz
11
Vose(sat)
-
0.2
0.5
-
0.2
0.5
V
7
VCE(s.t)
0.33
0.22
0.5
0.33
0.22
0.5
-
50
-
-
50
pA
-
100
%
100
kHz
(VCC = 15 V)
Minimum Output Frequency
(VCC = 15 V)
Oscillator Output Saturation Voltage
1114 sink = 5.0 mAl
OUTPUT SECTION
Output Saturation Voltage
V
8
ICE
-
9
9
APW
0
0
AOT
0
-
100
Dead Time Adjustment Range
100
0
Temperature Coefficient of Dead Time
-
TCOT
-
0.1
-
0.1
-
%
%/oC
12,13
14
118
-
5.0
15
-
5.0
15
I'A
liB
-
10
30
-
10
30
"A
(I L = 40 mA, Thigh to Tlow)
(IL = 25 mA, Thigh to Tlow)
Output Leakage Current
-
-
(VCE = 40 V, pins 11 and 13)
COMPARATOR SECTION
Pulse Width Adjustment Range
Comparator Bias Currents
255
MC3420, MC3520
ELECTRICAL CHARACTERISTICS (continued)
Characteristic
AUXILIARY INPUTS/OUTPUTS
Ramp Voltage
V
5
Peak High
Peak Low
Ramp Voltage Change
5
Vrarnp(Hil
V ra!11Qj Low I
aV ramp
5.5
2.0
6.0
2.4
6.5
2.8
5.5
2.0
6.0
2.4
6.5
2.8
3.0
3.5
4.0
3.0
3.5
4.0
V
3.0
-
rnA
-
40
",A
(V ramp Hi - V ramp Low)
Ramp Out Sink Current
5
'sink
Ramp Out Source Current
5
10
'source
-
3.0
-
IIH
-
-
40
-
10
IlL
-
-25
-180
-
-25
-180
",A
10
ISY/H
-
-
40
-
-
40
",A
10
ISY/L
-
-10
-180
-
-10
-180
",A
-
'source
-
2.0
-
-
2.0
-
mA
40
-
-
ns
150
-
ns
275
275
-
±1.0
-
ns
±1.0
-
40
150
Inhibit Input Current - High
400
",A
400
(VIH = 2.0 VI
Inhibit Input Current - Low
(VIL = 0.8 VI
Symmetry Correction Input/Output 2 Inhibit Current - High
(VSY = 2.0 V, pin 161
Symmetry Correction Input/Output 2 Inhibit Current - Low
(VSy=0.8V,pin161
F/F out Source Current
OUTPUT AC CHARACTERISTICS (TA = Thigh, VCC = +15 V, f -- 20 kHzl
Rise Time
15
Fall Time
15
'r
If
Overlap Time
15
lov
-
Assymmetry
(Duly Cycle = 50%1
15
tonl -t on 2
-
ton1
'.
NOTE:
Thigh = +125 0 C for MC3520
+70 o C for MC3420
Tlow = -55°C for MC3520
OoC for MC3420
FIGURE 2-EQUIVALENT CIRCUIT
Ramp
Ramp
Out
In
PWM
Vcontrol
Oscillator
Output
Out
Vce
5
8
Dead
Time
Adjust
2
9
V ref
Rext
3
Cext
12
F IF
15
Ground
Inhibit
Out
16
Symmetry
Correction
Input/Output 2 Inhibit
256
%
~
o
~
FIGURE 3 - CIRCUIT SCHEMATIC
(continued next page)
~
n
w
@
~~
~
~
J
): ~~
a
r
~
-...J
';j~
~ r
r
18k
'"
~
t.
~
40 k
36 k
7.0
k
~
~
~
r
>--
::: ,~~'(J ~
~ ~ ~
30 k
®
Vref
~
( )
I"
"-I
':oi ~
round
~
~
20 k
I"
~
@
r
ho
2.0
k
(J'I
B
2.0 k
r
4.0 k
N
A
~
30 k
:"I~
K
~~
6.8 k
~
~
~
r-1
A
.{~
y-----<
20 k
ho
l
~
I-~
I"
III
~
.~
c
10
k
AExternal
CD
o
0
6
Ce xternal
@),
R, mp
Out
~
o
3:
o
(continued)
~
FIGURE 3 - CIRCUIT SCHEMATIC
3:
n
w
A
B
~
~.
~
~
r=1JC~
I
tlll61
L-
ex>
20
k
>-<>--
~
--t
20
k
:!
:!Ii':
:!!':
~
c
Io
10
k
~
7.5
k
10 k
~
rl
10
k
",R~
(
30 k
CD
0
Dead Time
PWM
Out
0
1 8:"
V
K
Ramp
1.6 k
10 k
I'"
F"'
@
V
~:2
10 k
~
--<
-C
--<
r
I
F/Fout
Adjust
In
~
2.0 k
10 k
D
®
r-
~
V
@
Oscillator
Output
@ @
Inhibit
@
Output'
I--<
o.J
30 k
..,
-t
2.0
k
I--<
~>---
---<
~
VControl
V
r-
{
-t
-C
r-C
.,.
IIoJ
1
~
10 k
'"~
4.0
k
Ii':
cD
~
o
IIoJ
I"
10 k
~
N
U1
(r1
100
JG
1.6j
10 k
-COutput 2 Inhibit/
Symmetry Correction Input
MC3420, MC3520
GENERAL INFORMATION
The internal block diagram of the MC3420 is shown in
Figure 2, and consists of the following sections:
Dead Time Comparator
An additional comparator has been included in MC3420
to allow independent adjustment of system dead time or
maximum duty cycle. By dividing down Vref at Pin 9
with a resistive divider or potentiometer, and applying
this voltage to Pin 7, a stable dead time is obtained for
Voltage Reference
A stable reference voltage is generated by the MC3420
primarily for internal use. However, it is also available
externally at Pin 9 (V ref) for use in setting the dead
time (Pin 7) and for use as a reference for the external
control loop error amplifiers.
prevention of inverter switching transistor cross conduc-
tion at high duty cycles due to storage time delays.
Phase Splitter
Ramp Generator
A phase splitter is included to obtain two 1800 out of
phase outputs for use in multiple transistor inverter
systems. It consists of a toggle flip·flop whose clock
signal is derived by "AN Ding" the output of the PWM
The ramp generator section produces a symmetrical
triangular waveform ramping between 2.4 V and 6.0 V,
with frequency determined by an external resistor (Rext)
and capacitor (Cext) tied from Pins 1 and 2, respectively,
to ground,
comparator and a signal from the ramp generator section.
This "AND" gate ensures that the outputs truly alternate
under control loop transient conditions. Better under·
standing of this feature and MC3420 operation may be
gained by studying the circuit waveforms, shown in
Figure 4.
PWM Comparator
The output of the ramp generator at pin 8 is normally
connected to Pin 5, RAMP IN. The PWM (pulse width
modulation) comparator compares the voltage at Pin 6
(V control) to the ramp generator output. The level of
Vcontrol determines the outputs' pulse width or duty
cycle. The duty cycle of each output can vary, exclu·
sive of dead time, from 50% (when Vcontrol is at
approximately 2.4 V) to 0% (Vcontrol approximately
6.0 V),
FIGURE 4 - INTERNAL WAVEFORMS
~6.0
Voltage at
V
Veon'rol IL_ _ _ _ _
'--_Voltage at
Dead Time
J
Adjust
Operation (Constant Power
Supply Input Voltage & Load)
Pulsed" OutPuts During
Transient Conditions
By Use of AND Gate
At F/F Clock Input
• High Level Corresponds to
(Transient Output Load)
Output Transistor
Saturation
Ramp In, Ramp Out Tied Together (Pins 8 & 5)
PWM Out, Output 2 inhibit Tied Together (Pins 4 & 16)
259
MC3420, MC3520
FIGURE 5 - STANDARD AC. DC TEST CIRCUIT
+15 V
o
+)0 V 0
+30 V
10 k
0.0025
"F
10 k
14
11
1.0 k
13
1.0 k
15
+5.0 V
O.l1'F1;'
12
TTL-Compatible
FrequencV Meter
FIGURE 6 - FREQUENCY LIMIT TEST CIRCUIT
"B.O k
",
+15 V
5.0 k
O.l1'F~
4
10
10 k
16
500
pF
\. f
max
l'
14
11
1.0 k
13
1.0 k
15
20k~t----,
+5.0 V
O.l1'F*
12
FIGURE 7 - OUTPUT SATURATION TEST CIRCUIT
+10 V 0
+30
O.l1'F1'
10 k
10
4
16
2
11
14
760
lW
n.
15
13
Note: Use voltage change on pins 6, 7 to change output states.
A voltage must always be present on pins 6 and 7.
260
760
1W
n,
MC3420, MC3520
FIGURE 8 - OUTPUT LEAKAGE TEST CIRCUIT
+10 V 0
+30 V
-::;r
0.1 ~F
10
10k
16
4
14
10 k
11
15
10 k
13
+40 V
0.1 JJFl'
Note: A voltage
must always be
applied to
pins 6 and 7.
0+5.0 V
FIGURE 9 - OUTPUT DUTY CYCLE TEST CIRCUIT
+30 V 0
+10
0.1 ~F
10 k
'J
0.0025 J.l.F
10 k
10
16
4
11
14
1.0 k
15
+5.0 V
1.0 k
13
,-__0.'.' ~F
'J
+1.0 V
TYPICAL DUTY CYCLE
DEAD TIME VOLTAGE
VO',U5
PIN 7.
DEAD TIME
VOLTAGE (VI
% DUTY
CYCLE
(FOR EACH
(Vcontrol = 2.0 VI OUTPUT!
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
6.0
50
46
40
33
26
18
11
4.0
0
TYPICAL DUTY CYCLE
V6
versus PWM VOLTAGE (Vcontrol)
PIN 6.
CYCLE
V control (V)
(FOR EACH
(DEAD TIME
OUTPUT)
VOLTAGE: 1.0 VI
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
6.0
50
46
40
33
26
18
11
V7
Volts
% DUTY
100% Adjust
Dead Time
1.0
1.0
Pulse Width
1.0
1.0
Dead Time
7.0
1.0
Pulse Width
1.0
7.0
(Pin 11
+ Pin 13
Logic "1 ")
0% Adjust
(Pin 11 HPin 13)
NOTE: Logic "'" is TTL-Compatible VOH.
4.0
0
261
Logic " ' "
MC3420, MC3520
FIGURE 10 - INHIBIT/SYMMETRY rEST CIRCUIT
-=-
+30 V
o
VSY
1
0.1 ;tF-:;;J;'
10 k
10
14
11
1.0 k
15
1.0 k
13
+5.0 V
+1.0 V
20k~,---------.o
VI--==-
I
FIGURE 11 - OSCILLATOR OUTPUT (pin 14) TEST CIRCUIT
+30 V
o
+30 V
5.6 k
+10 V
10 k
0.1 ; t F 1 '
10
4
0.0025 ;tF
16
14
11
1.0 k
13
1.0 k
15
+5.0 V
9
O.I;tFJ
12
-=
FIGURE 12 - VControl BIAS CURRENT TEST CIRCUIT
+30 vO
+10 V
0.1 ;tF-:;;J;'
10
10 k
4
16
14
11
1.0 k
13
1.0 k
15
9
20k~.-_+4~.~0_V~__~
12
+3.0 V
262
+5.0 V
MC3420, MC3520
FIGURE 13 - DEAD TIME BIAS CURRENT TEST CIRCUIT
+30 V 0
+10 V
0.1 ~F
1;'
4
10
10 k
16
'4
11
1.0 k
'3
1.0 k
15
20 k
+4.0 V
TA" 125°:""'--
z
o
>=
~0S/":
~ 0.2
......- V
'";Ji
I--
/
~
~ 0.1
1/ /
o
lii
~ 0
>
../
;:/"
~
w
'"
~
V
o
~
V
a
10
7.6
40
30
20
IL, LOAD CURRENT (rnA)
a
0.5
1.5
1.0
lref, REfERENCE CURRENT ImA)
2.0
FIGURE 19 - PEAK FLIP-FLOP out VOL TAGE
versus EXTERNAL RESISTANCE
8.0
~
14
;5 7. a
~
13
~
12
15
~ 11
---......
t'---...
~
6.0
~>
5.0
~ 4. a
"-
2
10
o
9. 0
" 2. 0
~
8. 0
0
10
15
Rext , EXTERNAL RESISTANCE (kn)
20
'\
"
Q.
Z
5.0
I~
~
B
~
r-
~ 7.7
15
I--
-
--
~ 7.8
~- t - -
FIGURE 18 - DRAIN CURRENT versus
EXTERNAL RESISTANCE
1
I
VCC"15V
)- TA" 25°C
~
V/
o
3. 0
i'.,
i'--
I-
-
5.0
25
10
15
Rext , EXTERNAL RESISTANCE (kn)
20
25
FIGURE 21 - REFERENCE VOLTAGE TEMPERATURE
COEFFICIENT versus OUTPUT CURRENT
FIGURE 20 - DRAIN CURRENT versus TEMPERATURE
15
r--r--t-VCC"30V
Rext = 10 k
120
---I---..
.r-
~
VCC"30V
...-:::~
~
.& ~/'r\
/"
r- -:::::r--25
+25
+50
+75
+100
+125
TA, AMBIENT TEMPERATURE (OC)
30
0.01
1
VCC" 10 V
I IJll
NOTt loiJltilHAS NEGATIVE
TEMPERATURE COEffnEn
oF-'"
II
-50
V~" 15 V
III
0.1
1.0
REfERENCE OUTPUT CURRENT ImA)
264
10
MC3420, MC3520
OPERATION AND APPLICATIONS INFORMATION
The Voltage Reference
Dead Time
The temperature coefficient of V ref has been optim ized
for a 400!1A (""20 kn) load. If increased current capability is required, an op amp buffer may be used, as
shown in Figure 22.
Figure 24 illustrates how to set or adjust the MC3420
outputs' dead time or maximum duty cycle. For mini·
mum dead time drift with temperature or supply voltage,
VD.T. should be derived from V ref as shown.
FIGURE 22
FIGURE 24
)
9
Vref
/
;..
vref
~(VD.T.-2)
a
4
where fa is the output
frequency
20 kil
(':DT~
I
20 U1.
Dead Time "'"
R
7
Dead Time
Adjust
Connections to the V control Pin
Output Frequency
In many systems, it is necessary to make multiple connections to the V control Pin in order to implement
The values of Rext and C ext for a given output frequency,
fa, can be found from:
fa ""R
°C·55
ext
ext
features in addition to voltage regulation such as current
limiting, soft start, etc. These can be made by the use of
a simple "diode-OR" connection, as shown in Figure 25.
This allows whichever control element is seeking the
lowest PWM duty cycle to dominate. Note that are·
sistor. R 1, whose value is';;; 50 kn is placed from the
Vcontrol Pin to ground. This is necessary to provide a dc
path for the PWM comparator input bias current under
all conditions.
; 5.0 kn ,;;; Rext ,;;; 20 kn (Eq. 1)
or from the graph shown in Figure 23.
Note that fa refers to the frequency of Output 1 (Pin
11) or Output 2 (Pin 13). The frequency of the ramp
generator output waveform at Pin 8 will be twice f o _
The system duty cycle is given by:
FIGURE 23
5
D.C. (%) ""
\
51----
\
¥1?
f-- -
.~ ' - -
~.~
'<'-"
+I'~
"'2k
~/~-~~
'b
+"''b
10 k
"'"
X 100
(Eq.2)
FIGURE 25
l---~A'-\:''b~A'
~-"
.~-
VControl - 2
4
"- '-.
20 k
IN4148's
.--+.-_to
-
50ft
start circuit
+--o6 __.....-+----I...- _ t o voltage control
circuit
Rl
100 k
A1";;SO kr!
'0' OUTPUT FREQUENCY (Hzl
265
'--114-- ~~r~~~;ent limit
MC3420, MC3520
FIGURE 27
Soft Start
In most PWM switching supplies, a soft start feature is
desired to prevent output voltage overshoots and magnetizing current imbalances in the power transformer
primary. This feature forces the duty cycle of the
switching elements to gradually increase from zero to
their normal operating point during initial system powerup or after an inhibit. This feature can be easily implemented with the MC3420. One method is shown in
Figure 26,
Q1
110
Vac
+ \to power
e1
Rectifiers
I-------..---il.
f
~witching
sectIon
FIGURE 26
to provide a time delay on the inhibit pin to keep it low
until the input filter capacitor, C1, has had time to
charge, whereas the initial portion of the soft start
timing cycle can be used for this delay if this signal is
derived from one of the output pins. However, using the
Oscillator Output Pin does offer the advantage that its
waveform has a constant 50% duty cycle, independent
of the outputs' duty cycle which can simplify the design
of a drive circuit for T1.
Vee
D1
To Voltage
15
&
- - -}
- --
R1~50
kn
Current
Control
Loops
04 01 - 04. IN4148
Slaving
I n some applications, as when one PWM inverter/converter is used to feed another, it may be desired that
their frequencies be synchronIZed. This can be done
with multiple MC3420s as shown in Figure 28. 8y
omitting their Rext and Cext, up to two MC3420s may
be slaved to a master MC3420.
After an inhibit command or during)power-up, the voltage on R 1 and Pin 6 exponentially decays from VCC
toward ground with a time constant of R1C1, allowing a
gradual increase in duty cycle. Diodes D2 - D4 provide
a diode-or function at the Vcontrol Pin, while 01 serves
to reset the timing capacitor, C 1, when an inhibit command is received thereby reinitializing the soft-start
feature. D1 allows C1 to reset when power (VCC) is
turned off.
FIGURE 28 - SLAVING THE MC3420
89-------~------------_.--_,
Aext
FIF
Out
C ext
8
Inrush Current Limiting
I
Since many PWM switching supplies are operated directly
off the rectified 110 Vac line with capacitive input
filters, some means of preventing rectifier failure due to
inrush surge currents is usually necessary. One method
which can be used is shown in Figure 27.
In this circuit, a series resistor, RS' is used to provide
inrush surge current limiting. After the filter capacitor,
C 1, is charged, 01 receives a trigger signal from the control circuitry through T1 and shorts RS out of the circuit, eliminating its otherwise, larger power dissipation.
The trigger signal for 01 may be derived from either the
oscillator output (Pin 14) or one of the MC3420's outputs. If the oscillator output is used, it will be necessary
266
®
MC3423
MC3523
MOTOROLA
Specifications and Applications
InforIllation
OVERVOLTAGE
SENSING CIRCUIT
OVERVOL TAGE "CROWBAR" SENSING CIRCUIT
SILICON MONOLITHIC
INTEGRATED CIRCUIT
These overvoltage protection circuits (OVP) protect sensitive electronic circuitry from overvoltage transients or regulator failures
when used in conjunction with an external "crowbar" SCR_ They
sense the overvoltage condition and quickly "crowbar" or short
circuit the supply, forcing the supply into current limiting or opening the fuse or circu it breaker.
The protection voltage threshold is adjustable and the MC3423/
3523 can be programmed for minimum duration of overvoltage
condition before tripping, thus supplying noise immunity.
The MC3423/3523 is essentially a "two terminal" system, therefore it can be used with either positive or negative supplies.
P1 SUFFIX
PLASTIC PACKAGE
CASE 626
(MC3423 only)
USUFFIX
CERAMIC PACKAGE
CASE 693
MAXIMUM RATINGS
Rating
Differential Power Supply Voltage
f-=---
SeAse Voltage (1)
Sense Voltage (2)
Remote ActivatIOn Input Voltage
Symbol
Value
Unit
Vee-VEE
V Sense 1
40
Vdc
6.5
Vdc
VS ense 2
V aet
6.5
Vdc
7.0
Vdc
300
rnA
Output Current
10
Operating Ambient Temperature Range
MC3423
MC3523
TA
Operating Junction Temperature
TJ
Plastic Package
o to +70
-55 to +125
.~
1
'e
PIN CONNECTIONS
'e
125
150
Ceramic Package
Storage Temperature Range
T stg
-65 to +150
°e
Indicator
Output
Remote
Activation
Current
Source
(top view)
TYPICAL APPLICATION
V out
Current
Limited
ORDERING INFORMATION
Q1
DC
Power
C out
DEVICE TEMPERATURE RANGE PACKAGE
Supply
MC3423P1
MC3423U
MC3523U
NOTE: A 2N6504 or equivalent is suggested for 01.
267
o to +70 o C
o to +70o C
-55 to +125° C
Plastic DIP
Ceramic DIP
Ceramic DIP
MC3423, MC3523
ELECTRICAL CHARACTERISTICS (5 V .. VCC -VEE" 36 V, Tlow < TA < Thigh unl... otherwise notad.)
Characteristic
SupplV Voltage Range
Svmbol
Min
TVp
Max
VCC·VEE
4.5
-
40
Vdc
Vo
VCC·2.2
VCC·l.S
-
Vdc
VOL(lnd)
-
0.1
0.4
Vdc
VSense I,
VSense 2
TCVSl
2.45
2.6
2.75
Vdc
IIH
IlL
-
Isource
0.1
Output Voltage
(10 = 100mA)
Indicator Output Voltage
(lO(lnd) = 1.6 mAl
Sense Voltage
(TA = 25 0 C)
Temperature Coefficient of VSense 1
Unit
%/vC
0.06
(Figure 2)
Remote Activation Input Current
(VIH
(VIL
itA
= 2.0 V, VCC-VEE = 5.0 V)
= O.S V, VCC-VEE = 5.0 V)
Source Current
Output Current Risetime
(TA
40
-ISO
0.2
0.3
400
tr
= 25 0 C)
5.0
-120
Propagation Delay
(TA = 25 0 C)
tpd
Supply Current
MC3423
MC3523
ID
-
0.5
-
-
6.0
5.0
10
7.0
Tlow =
C for MC3523
Thigh = +125 0 C for MC3523
= + 70°C for MC3423
= OoC for MC3423
FIGURE 1 - BLOCK DIAGRAM
Vee
Current
4 Source
2
V sense 1 0-1--11----
'---4>--j---O Output
8
VEE
3
V sense 2
5
6
Remote
Activation
Indicator
Output
FIGURE 2 - SENSE VOLTAGE TEST CIRCUIT
Vee
Switch 1
(A) __-----------=2~
(8)_---.-.....::--1
ItS
mA
-550
mA
mA/lts
8
VSense 1
VSens8 2
Ramp VI until output gOBS high; this Is
the VS anse threshold.
268
MC3423, MC3523
r" '
FIGURE 3 - BASIC CIRCUIT CONFIGURATION
,-
+~
Fl
I
I
(+ Sense
Lead)
Rl
I
I
I
I
1
01
2
Power
Supply
'---:l
t:::
R2
4
MC3523
V tnp '" Vref
I
~
I
To
I
~
Load
I
RG
(~Sense
"" 2.6 V
(1+~)
For minimum value of RG, see Figure 9
,
r;;'.
7~
(1+~)
R2';;; 10 kH for minimum drift
Q1 is 2N6504 or equivalent
·See text for explanation
I
I
Lead)
FIGURE 4 - CIRCUIT CONFIGURATION FOR SUPPLY VOLTAGE ABOVE 36 V
(+ Sense
Lead)
Rl
IN4740
Power
Supply
To
Load
MC3523
10 V
MC3423
10l'F
15 V
3
RS
=
Vtrip
(Vs 2~ 10) Ul
~
Vref
(1+~)
::::;: 2.6 V
(1+~)
*R2';;;; 10 kn
L-----r-,---~·R2
Q1
VS':;;; 50
V; 2N6504 or equivalent
Vs ~
Vs ~
Vs ~
VS ~
VS';;;;
v,
V,
V.
V,
V,
lOa
200
400
600
800
2N6505
2N6506
2N6507
2N6508
2N65Q9
or equivalent
or equivalent
or equivalent
or equ ivalent
or equivalent
FIGURE 5 - BASIC CONFIGURATION FOR PROGRAMMABLE DURATION OF
OVERVOLTAGE CONDITION BEFORE TRIP
,------1--------~~~--------~---+VCC
Vc
Vref-t--~-----7-
Rl
2N6504 or
equivalent
n
__ L_~
o
-
____
Vo
R2
o
~ ~----
-----+---------,
L - - , - - I
td
R3 ~ Vtrip
~10mA
td
269
=
Vref xC"'=:: [12x103] C (See Figure 10)
Isource
MC3423, MC3523
APPLICATIONS IN FORMATION
BASIC CIRCUIT CONFIGURATION
The basic circuit configuration of the MC3423/3523
OVP is shown in Figure 3 for supply voltages from 4.5 V
to 36 V, and in Figure 4 for trip voltages above 36 V. The
threshold or trip voltage at which the MC3423/3523 will
trigger and supply gate drive to the crowbar $CR, 01, is
determined by the selection of R 1 and R2. Their values
can be determined by the equation given in Figures 3 and
4, or by the graph shown in Figure 8. The minimum value
of the gate current limiting resistor, RG, is given in
Figure 9. Using this value of RG, the SCR, 01, will receive
the greatest gate current possible without damaging the
MC3423/3523. If lower output currents are required, RG
can be increased in value. The switch, Sl, shown in Figure
3 may be used to reset the SCR crowbar. Otherwise, the
power supply, across which the SCR is connected, must
be shut down to reset the crowbar. If a non currentlimited supply is used, a fuse or circuit breaker, F 1,
should be used to protect the SCR and/or the load.
The circuit configurations shown in Figures 3 and 4
will have a typical propogation delay of 1.0 J1S. If faster
operation is desired, pin 3 may be connected to pin 2 with
pin 4 left floating. This will result in decreasing the propogation delay to approximately 0.5 J1S at the expense of a
slightly increased TC for the trip voltage value.
FIGURE 6 - CONFIGURATION FOR PROGRAMMABLE
DURATION OF OVERVOL TAGE CONDITION BEFORE
TRIP/WITH IMMEDIATE TRIPAT
HIGH OVERVOL TAGES
(+ Sense
Lead)
+
-
1
Rl
2
ZI
l
Power
Supply
I
~
MC3523
R2
~
01
5
lK
41
7
T
C
(- Sense Lead)
-
ADDITIONAL FEATURES
1. Activation Indication Output
An additional output for use as an indicator of OVP
activation is provided by the MC3423/3523. This output is an open collector transistor which saturates
when the OVP is activated. It will remain in a saturated
state until the SCR crowbar pulls the supply voltage,
VCC, below 4.5 V as in Figure 5. This output can be
used to clock an edge triggered flip-flop whose output
inhibits or shuts down the power supply when the OVP
trips. This reduces or eliminates the heatsinking requ irements for the crowbar SC R.
CONFIGURATION FOR PROGRAMMABLE MINIMUM
DURATION OF OVERVOLTAGE CONDITION
BEFORE TRIPPING
In many instances, the MC3423/3523 OVP will be used
in a noise environment. To prevent false tripping of the
OVP circuit by noise which would not normally harm the
load, MC3423/3523 has a programmable delay feature. To
implement this feature, the circuit configuration of Figure
5 is used. In this configuration, a capacitor is connected
from pin 3 to VEE. The value of this capacitor determines
the minimum duration of the overvoltage condition which
is necessary to trip the OVP_ The value of C can be found
from Figure 10. The circuit operates in the following
manner: When VCC rises above the trip point set by R1
and R2, an internal current source (pin 4) begins charging
the capacitor, C, connected to pin 3. If the overvoltage
condition disappears before this occurs, the capacitor is
discharged at a rate 3> 10 times faster than the charging
rate, resetting the timing feature until the next overvoltage
condition occurs.
Occasionally, it is desired that immediate crowbarring
of the supply occur when a high overvoltage condition
occurs, while retaining the false tripping immunity of
Figure 5. In this case, the circuit of Figure 6 can be used_
The circuit will operate as previously described for small
overvoltages, but will immediately trip if the power
supply voltage exceeds VZ1 + 1.4 V.
2. Remote Activation Input
Another feature of the MC3423/3523 is its remote
activation input, pin 5. If the vol age on this CMOS/TTL
compatible input is held below 0.8 V, the MC3423/
3523 operates normally. However, if it is raised to a
voltage above 2.0 V, the OVP output is activated
independent of whether or not an overvoltage condition is present. It should be noted that pin 5 has an
internal pull-up current source. This feature can be
used to accomplish an orderly and sequenced shutdown of system power supplies during a system
fault condition. In addition, the activation indication
output of one MC3423/3523 can be used to activate
another MC3423/3523 if a single transistor inverter is
used to interface the former's indication output to
the latter's remote activation input, as shown in
Figure 7. In this circuit, the indication output (pin 6)
of the MC3423 on power supply 1 is used to activate
the MC3423 associated with power supply 2. 01 is
any small PNP with adequate voltage rating.
270
MC3423, MC3523
FIGURE 7 - CIRCUIT CONFIGURATION FOR
ACTIVATING ONE MC3523 FROM ANOTHER
I
Power
Supply
#1
I
+
c~
R1
FIGURE 8 - R1 versus TRIP VOLTAGE
30
/
20
V
'-'
J
Power
Supply
#2
I
C'
~1
+
V
V",," V
V
V
'"
1;:;
~
'"-'
V
V
V V
Z
,,,,9 V
V
R2=27k
~w
10 k
"'~
V V
./. v./
10
~ 'l"
~~
~
1 k
-
o
o
50
10
15
10
15
30
Vr, TRIP VOLTAGE 1VOLTSl
Note that both supplies have their negative output
leads tied together (i.e., both are positive supplies). If
their positive leads are common (two negative supplies)
the emitter of 01 would be moved to the positive lead
of supply 1 and R1 would therefore have to be resized
to deliver the appropriate drive to 01.
FIGURE 9- MINIMUM RG versus SUPPLY VOL TAGE
5
30
~o
CROWBAR SCR CONSIDERATIONS
-
I_
r
V
>
Referring to Figure 11, it can be seen that the crowbar
SCR, when activated, is subject to a large current surge
from the output capacitance, Cout 1. This surge current is
illustrated in Figure 12, and can cause SCR failure or
degradation by anyone of three mechanisms: di/dt,
absolute peak surge, or 12t. The interrelationship of these
failure methods and the breadth of the application make
specification of the SCR by the semiconductor manu·
facturer difficult and expensive. Therefore, the designer
must empirically determine the SCR and circuit elements
which result in reliable and effective OVP operation.
However, an understanding of the factors which influence
the SCA's di/dt and surge capabilities simplifies this task.
"
15
~
i
U
~
/'
/
RGIMIn)- 0
If Vee < 11 V
/"
/"
~
./
20
./
15
....... V
/'
10
o
10
.-f---- --
40
30
50
10
60
RG. GATE CURRENT lIMlTlNG RESISTOR (OHMS)
70
80
FIGURE 10 - CAPACITANCE versus
MINIMUM OVERVOLTAGE DURATION
1.0
1. di/dt
As the gate region of the SCR is driven on, its area
of conduction takes a finite amount of time to grow,
starting as a very small region and gradually spreading.
Since the anode current flows through this turned~on
gate region, very high current densities can occur in
the gate region if high anode currents appear quickly
(di/dt). This can result in immediate destruction of
the SCR or gradual degradation of its forward blocking
voltage capabilities - depending on the severity of the
occasion.
o. 1
0.0 1
0.00 1
V
0.0001V
0.001
1Cout consists of the power supply output caps, the
load's decoupling caps, and in the case of Figure 11 A, the
supply's input filter caps.
0.01
0.1
to DELAY TIME (ms)
271
1.0
10
MC3423, MC3523
The value of di/dt that an SCR can safely handle is
influenced by its construction and the characteristics
of the gate drive signal. A center·gate·fire SCR has
more di/dt capability than a corner·gate·fire type and
heavily overdriving (3 to 5 times IGT) the SCR gate
with a fast « 1 f.1s) rise time signal will maximize its
di/dt capability. A typical maximum number in phase
control SCRs of less than 50 Arms rating might be
200 A/f.1s, assuming a gate current of five times IGT
and < 1 f.1S rise time. If having done this, a di/dt prob·
lem is seen to still exist, the designer can also decrease
the di/dt of the current waveform by adding indue·
tance in series with the SCR, as shown in Figure 13.
Of course, this reduces the circuit's ability to rapidly
reduce the de bus voltage and a tradeoff must be made
between speedy voltage reduction and di/dt .
FIGURE 11 - TYPICAL CROWBAR OVP CIRCUIT
CONFIGURATIONS
11A
V out
DC
+
Power
C out
Supplv
'-------,_-'
11B
V out
Reset
• Needed if supply not current limited
2. Surge Current
FIGURE 12 - CROWBAR SCR SURGE CURRENT
WAVEFORM
If the peak current and/or the duration of the surge
is excessive, immediate destruction due to device
overheating will result. The surge capability of the SCR
is directly proportional to its die area. If the surge
current cannot be reduced (by adding series resistance
- see Figure 13) to a safe level which is consistent with
the system's requirements for speedy bus voltage
reduction, the designer must use a higher current SCR.
This may result in the average current capability of
the SCR exceeding the steady state current require·
ments imposed by the de power supply.
A WORD ABOUT FUSING
FIGURE 13 - CIRCUIT ELEMENTS AFFECTING
SCR SURGE & di/dt
Before leaving the subject of the crowbar SCR, a few
words about fuse protection are in order. Refering back to
Figure 11 A, it will be seen that a fuse is necessary if the
power supply to be protected is not output current limi·
ted. This fuse is not meant to prevent SCR failure but
rather to prevent a fire!
In order to protect the SCR, the fuse would have to
possess an 12 t rating less than that of the SCR and yet
have a high enough continuous current rating to survive
normal supply output currents. In addition, it must be
capable of successfully clearing the high short circuit
currents from the supply. Such a fuse as this is quite
expensive, and may not even be available.
Output
Cap
R & L EMPIRleALLY DETERMINEDI
CROWBAR SCR SELECTION GUIDE
As an aid in selecting an SCR for crowbar use, the
following selection guide is presented.
The usual design compromise then is to use a garden
variety fuse (3AG or 3AB style) which cannot be relied on
to blow before the thyristor does, and trust that if the
SCR does fail, it will fail short circuit. In the majority of
the designs, this will be the case, though this is difficult to
guarantee. Of course, a sufficiently high surge will cause
an open. These comments also apply to the fuse in Figure
11B.
272
DEVICE
IRMS
ITSM
PACKAGE
2N6400 Series
2N6504 Series
2N 1842 Series
2N2573 Series
2N681 Series
MCR3935·1 Series
MCR81·5 Series
16A
25A
16A
25A
25A
35A
80A
160A
160A
125A
260A
200A
350A
1000A
T0220 Plastic
T0220 Plastic
Metal Stud
Metal TO·3 Type
Metal Stud
Metal Stud
Metal Stud
®
MC3424 • MC3424A
MC3524 • MC3524A
MC3324 • MC3324A
MOTOROLA
Product Preview
POWER SUPPLY SUPERVISORY CIRCUITI
DUAL VOLTAGE COMPARATOR
The MC3424 series is a dual-channel supervisory circuit, consisting of two uncommitted input comparators, a reference, output comparators, and high-current drive and indicator outputs for
each channel. The input comparators feature programmable hysteresis, high common-mode rejection, and wide common-mode
range, capable of comparing at ground potential with single-supply operation. Separate delay-filter pins are provided to increase
noise immunity by delaying activation of the outputs. A 2.5 V
bandgap voltage reference is pinned-out for referencing the input
comparators, or other external functions. Independent high-current drive and indicator outputs for each channel can source and
sink up to 300 mA and 50 mA resp'ectively. CMOSITTL compatible
digital inputs provide remote activation of each channel's outputs.
An input-enable pin allows control of the input comparators.
Although this device is intended for power supply supervision,
the pinned-out reference, uncommitted-input comparator, and
many other features, enable the MC3424 series to be utilized for
a wide range of applications.
• Pinned-Out 2.5 V Reference
• Wide Common-Mode Range
• Programmable Hysteresis
• Programmable Time Delays
• Two 300 mA Drive Outputs
• Remote Activation Capability
• Wide Supply Range: 4.5 V"" VCC "" 40 V
• Low Current Drain
Applications
• Dual-Over Voltage "Crowbar" Protection
• Dual-Under Voltage Supervision
• Over/Under Voltage Protection
• Split-Supply Supervision
• Line-Loss Sensing
• Proportional Control
• Over/Under-Speed Indicator
• Sequential-Time Delay
• Battery Charging
POWER SUPPLY SUPERVISORY
CIRCUIT IOUAL VOLTAGE
COMPARATOR
SILICON MONOLITHIC
INTEGRATED CIRCUIT
L SUFFIX
CERAMIC PACKAGE
CASE 620
PIN CONNECTIONS
Vre !
Enable
Select 1/C1 +
C2DLY2
IND 2
IND 1
TYPICAL APPLICATION
Over-Voltage Crowbar Protection, Under-Voltage Indication
.....---....---.....-c v out
I-~.---.>-
Gnd
DRV1
(Top view)
Current
Limited
DC
Power
Supply
Co
Under-Voltage
Indication
ORDERING INFORMATION
Device
MC3524L, AL
MC3324L, AL
MC3324P, AP
This document contains Information on a product under development Motorola reserves the
right to change or discontinue this product without notice
273
MC3424L, AL
MC3424P, AP
Temperature
Range
Package
-55 to + 125'C Ceramic DIP
-40 to + 85'C
o to
+ 70'C
Ceramic DIP
Plastic DIP
Ceramic DIP
Plastic DIP
MC3424, MC3424A, MC3524, MC3524A, MC3324, MC3324A
FIGURE 1 -
POWER SUPPLY OVERVOLTAGE PROTECTION (CROWBAR)
AND LINE LOSS DETECTOR
Vin
+ va
15k
-=
50k
5
16
1.0!,1
10k
-=
IND2
11
C2+
20k
14
110VE]
60 Hz
RS
27 k
126 V CT
-=
MCR67-1
RAI VCC RA2
S
IE
ORVI
Cl-
2
CRI
1-
10k
12
Vrel
I
-=
9
Line Loss Indication
MC3524
Cl+
C2-
OLYI
4
Gnd
lOOI,,1
-=
-=
FIGURE 2 - OVERVOLTAGE PROTECTION, WITH DELAY, OF SPLIT SUPPLIES
USING SCR "CROWBAR" SHUTDOWN AND LATCHED-FAULT INDICATION.
(The Positive Sense is Chosen to Have IHRH Hysteresis Voltage.)
+VTRIP
~--------------------------------------,--o+Va
r---------------.-----------~~+5V
Rl
500
+VTRIP = Vrel (1 +
R4
-VTRIP = Vrel (R'3
Co = loto
Vrel
Rl
'R2)
-
1)
= 200 "A to
2.5 V
Fault -Va
9
VCC 2
Cl +
"
Latch!
Unlatch
R2
I----_"""'Ir-.,
o-.....---------=-t
11
MC3524
L-------------~.-~IND2
Vrel f-"____-.
0-_..::::..:..::...---=.;12"_1 RA2
~__________________'~O~O~!~I----S"_lORV'
C2+
120n
C2-
15
R3
14
03
R4
-=
274
-VTRIP
-Va
MC3424, MC3424A, MC3524, MC3524A, MC3324, MC3324A
MC3524/3424/3324 BLOCK DIAGRAM
VCC
9
+
+
Enable
Select 11
C1+ o--h_----I
2
+
~------~~-+------~+
C1 - o-3+-"1-_---i
Drive 1
8
Input
Enable
1.4 V
16
Output
Comparator~--....
C2+
C2-
~----~~r--+-t--t-~+
15
14
___
2
+
13
4
I 5 12
DLY2 DLY1 I RA1 RA2
I
INPUT SECTION
I
I
Note: All voltages and currents are nominal.
275
7
Vref
Gnd
OUTPUT SECTION
@
MC34060
MC35060
MOTOROLA
Specifications and Applications Information
SWITCH MODE PULSE WIDTH MODULATION
CONTROL CIRCUITS
SWITCHMODE
PULSE WIDTH MODULATION
CONTROL CIRCUITS
SILICON MONOLITHIC
INTEGRATED CIRCUITS
The MC35060 and MC34060 are low cost fixed frequency, pulse
width modulation control circuits designed prl merlly for single
ended SWITCHMODE power supply control. These devices feature:
•
Complete Pulse Width Modulation Control Circuitry
•
On-Chip OSCillator With Master or Slave Operation
•
On-Chip Error Amplifiers
•
On-Chip 5.0 Volt Reference
• Adjustable Dead Time Control
• Uncommitted Output Transistor for 200 mA Source or Sink
P SUFFIX
PLASTIC PACKAGE
CASE 646
PIN CONNECTIONS
Non-Inv
14
Input
Inv
Input
Non-Inv
Input
Inv
.
,.
Input
Campen PWM
Vref
Camp Input
Dead -Time
Control
-----
NC
14
VCC
1
C
l SUFFIX
CERAMIC PACKAGE
CASE 632
(TO-116)
Ground
(top view)
ORDERING INFORMATION
Temperature
The MC34060 is specified over the commercial operating range of
O°C to +70°C. The MC35060 IS specified over the full military range
of -55 to +125°C.
Device
Range
Package
MC35060L
-55 to + 125°C
Ceramic DIP
MC34060P
o to +70°C
a to +70°C
Ceramic DIP
MC34060l
276
PlastiC DIP
MC34060, MC35060
FIGURE 1 - BLOCK DIAGRAM
6
RT
eT
r
12
Reference
Oscillator
Ref Out
Regulator
Dead-Time
10
Vee
4
IDead-Time
",07
V
Control
9
01
=07 mA
8
Gnd
13
2
14
Error Amp
Feedback/ P W M
Error Amp
1
Comparator Input
2
7
FIGURE 2 -- TIMING DIAGRAM
Capacitor CT
Feedback P W M
Comparator
Oead-Tlme Control
Output 01,
Emitter
Description
The MC35060/34060 IS a fixed-frequency pulse width
modulation control circuit, Incorporating the primary
building blocks required for the control of a sWitching power
supply, (See Figure 1.1 An internal-linear sawtooth oscillator IS frequency-programmable by two external components, RTand CT The oscillator frequency IS determined by:
1,1
fosc= RT •
Output pulse Width modulation IS accomplished by comparIson of the positive sawtooth waveform across capacitor CT
to either of two control Signals The output IS enabled only
dUring that portion of time when the sawtooth voltage is
greater than the control Signals Therefore, an Increase In
control-signal amplitude causes a corresponding linear
decrease of output pulse Width (Refer to the timing diagram shown In Figure 2 I
(T
277
NtC34060,NtC35060
back pin varies from 0.5 to 3.5 V. Both error amplifiers have
a common-mode input range from -0.3 Vto (VCC -2 V), and
may be used to sense power supply output voltage and current. The error-amplifier outputs are active high and are
ORed together at the non-inverting input of the pulse-width
modulator comparator. With this configuration, the amplifier that demands minimum output on time, dominates
control of the loop.
The MC35060/34060 has an internal 5.0 V reference
capable of sourcing up to 10 mA of load currents for external
bias circuits. The reference has an internal accuracy of
±5% with a thermal drift of less than 50 mV over an
operating temperature range of 0 to +70°C.
The control signals are external inputs that can be fed into
the dead-time control, the error amplifier inputs, or the feedback input. The dead-time control comparator has an effective 120 mV input offset which limits the minimum output
dead time to approximately the first 4% of the sawtoothcycle time. This would result in a maximum duty cycle of
96%. Additional dead time may be imposed on the output by
setting the dead time-control input to a fixed voltage, ranging
between 0 to 3.3 V.
The pulse width modulator comparator provides a means
for the error amplifiers to adjust the output pulse width from
the maximum percent on-time, established by the dead time
time control input, down to zero, as the voltage at the feed-
MAXIMUM RATINGS (Full operating ambient temperature range applies unless otherwise noted)
Rating
Symbol
MC35060
MC34060
Unit
VCC
42
42
V
Collector Output Voltage
Vc
42
42
V
Collector Output Current
IC
250
250
mA
Amplifier Input Voltage
Vin
VCC + 0.3
VCC + 0.3
V
Power Dissipation @ TA';; 45°C
Po
1000
1000
mW
Operating Junction Temperature
TJ
150
150
°C
TA
-55 to 125
o to 70
°C
Tstg
-65 to 150
-65 to 150
°C
Svmbol
L Suffix
Ceramic Package
P Suffix
Plastic Package
Unit
ReJA
100
80
°C/W
I/ReJA
10
12.5
mW/oC
TA
50
45
°c
Power Supply Voltage
Operating Ambient Temperature Range
Storage Temperature Range
THERMAL CHARACTERISTICS
Characteristic
Thermal Resistance. Junction to Ambient
Power Derating Factor
Derating Ambient Temperature
RECOMMENDED OPERATING CONDITIONS
Condition/Value
Svmbol
Power Supply Voltage
VCC
MC35060/MC34060
Min
Typ
Max
7.0
15
40
Unit
-V
Collector Output Voltage
Vc
-
30
40
V
Collector Output Current
IC
-
-
200
mA
-
Vee -2.0
V
-
0.3
mA
Amplifier Input Voltage
Vin
Current Into Feedback Terminal
If.b.
-0.3
-
Reference Output Current
Iref
-
-
10
mA
Timing Resistor
RT
1.8
47
500
kll
Timing Capacitor
CT
0.00047
0.001
10
~F
fosc
1.0
25
200
kHz
Oscillator Frequency
278
MC34060, MC35060
ELECTRICAL CHARACTERISTICS vCC = 15 V. fosc = 25 kHz unless otherwise noted. For typical values TA = 25°C. for min/max
values TA is the operating ambient temperature range that applies unless otherwise noted.
Characteristic
REFERENCE SECTION
Reference Voltage
Vref
4.75
5.0
5.25
4.75
5.0
5.25
V
Reference Voltage Change with Temperature
(ATA = Min to Max)
Vref(.H)
-
0.2
2.0
-
1.3
2.6
%
Input Regulation
(VCC = 7.0 V to 40 V)
Regline
-
2.0
25
-
2.0
25
mV
Output Regulation
(10= 1.0 mAto 10 mAl
Regload
-
3.0
15
-
3.0
15
mV
10
35
50
-
35
-
mA
(10= 1.0mA)
_
.
Short-Circuit Output Current
(Vref=OV. TA= 25C)
ISC
OUTPUT SECTION
Collector Off-State Current
(VCC = 40 V. VCE = 40 V)
lC(off)
-
2.0
lOci
-
2.0
100
I'A
Emitter Off-State Current
(VCC = 40 V. Vc = 40 V. VE = 0 V)
IE(off)
-
-
-150
-
-
-100
I'A
Collector-Emitter Saturation Voltage
Common-Emitter
(VE = 0 V. IC = 200 mAl
Emitter-Follower
(VC = 15 V. IE = -200 mAl
Vsat(C)
-
1.1
1.5
-
1.1
1.3
V
Vsat(E)
-
1.5
2.5
-
1.5
2.5
V
Output Voltage Rise Time (TA = 2S'C)
Common-Emitter (See Figure 12)
Emitter-Follower (See Figure 13)
tr
-
100
100
200
200
-
100
100
200
200
ns
-
Output Voltage Fall Time (TA = 25°C)
Common-Emitter (See Figure 12)
Emitter-Follower (See Figure 13)
tf
25
40
100
100
-
25
40
100
100
ns
-
-
Characteristic
ERROR AMPLIFIER SECTIONS
Input Offset Voltage
(VO[Pin 3] = 2 5 V)
VIO
-
2.0
10
mV
Input Offset Current
(VC[Pin 3] = 2.5 V)
110
-
50
250
nA
Input Bias Current
(VO[Pin 3] = 2.5 V)
liB
-
0.1
1.0
I'A
Input Common-Mode Voltage Range
(VCC = 7.0 V to 40 V)
VICR
-0.3
-
VCC-2.0
V
Open Loop Voltage Gain
(AVO = 3.0 V. Va = 0.5 to 3.5 V. RL = 2.0 kll)
AVOL
70
95
-
dB
279
MC34060, MC35060
ELECTRICAL CHARACTERISTICS VcC: 15V, losc: 25 kHz unless otherwise noted. For typical values TA
values TA is the operating ambient temperature range that applies unless otherwise noted.
=25°C, lor minimax
Characteristic
ERROR AMPLIFIER SECTIONS (Continued)
Unity-Gain Crossover Frequency
(VO: 0.5, to 3.5 V, RL: 2.0 kll)
Ic
-
350
-
Phase Margin at Unity-Gain
(VO: 0.5 to 3.5 V, RL =20 kll)
m
-
65
-
deg.
CMRR
65
90
-
dB
PSRR
-
100
-
dB
Output Sink Current
(VO[Pin 3J : 0.7 V)
'0-
03
07
-
mA
Output Source Current
(VO[Pin 3J: 3.5 V)
10+
-2.0
-4.0
-
mA
VTH
-
35
45
V
,,-
0.3
0.7
-
mA
Input Bias Current (Pin 4)
(V in : 0 to 5 25 V)
"B(DT)
-
-20
-10
Maximum Output Duty Cycle
(V in = 0 V, CT= 0 1 ~F, RT= 12 kJl)
(Vin: 0 V, CT: 0.001 ~F, RT: 47 kll)
DC max
--
96
92
100
100
-
28
33
a
-
-
Common-Mode Rejection Ratio
(VCC =40V)
Power Supply Rejection Ratio
(~VCC: 33 V, Vo : 2.5 V, RL : 2.0 kn)
p"
kHz
PWM COMPARATOR SECTION (Test Circuit Figure 11)
Input Threshold Voltage
(Zero Duty Cycle)
Input Sink Current
(V[Pin 3J: 0 7 V)
DEAD-TIME CONTROL SECTION (Test CirCUit Figure 11)
%
90
Input Threshold Voltage (Pin 4)
(Zero Duty Cycle)
(MaXimum Duty Cycle)
~A
V
VTH
OSCILLATOR SECTION
Frequency
(CT = 0 001 ~F, RT = 47 kJl)
losc
-
25
-
kHz
Standard Deviation of Frequency*
(CT = 0 001 ~F, RT = 47 kJl)
afosc
-
3.0
-
%
Frequency Change with Voltage
(VCC = 7.0 V to 40 V, TA =25°C)
,/ltosc(LlV)
-
01
-
%
Frequency Change with Temperature
MosdLlT)
-
1.0
2.0
%
-
55
70
10
15
-
7.0
-
(:OTA ~ 25°C to TA low, 25°C to TA high)
TOTAL DEVICE
Standby Supply Current
(Pin 6 at Vrel, all other inputs and outputs open)
(VCC = 15 V)
(VCC: 40 V)
mA
ICC
Average Supply Current
(V[Pin 4J: 2.0 V, CT ~ 0.001, RT: 47kll). See Figure 11.
IS
"Standard deviatIOn IS a measure of the, statlstrcal dlstnbutlon about the mean as denved from the formula, a =
N
~ IXn - ~)2
n::: 1
---N-l
280
mA
MC34060, MC35060
FIGURE 4 - OPEN LOOP VOLTAGE GAIN AND PHASE
versus FREQUENCY
FIGURE 3 - OSCILLATOR FREQUENCY
versus TIMING RESISTANCE
300k
r-
~
15
:::>
~~
15 V
"'-...
' " AVOL
'" 60
~
@
fl:
::':~i f:=f-
!5
~
~
~ 80
z
~ 70
f ~l
k
51
0
z
~ 30
§
20
il
10""
it
100
JO'k
2k
5k
10k
20k
10k
lOOk
200k
500k
""
10
1M
100
Ik
::>
::>
0
:go
0:;:
Q
::l
Q
...a5
ffi
......
u
'
-
-
VCC=15V
VIPIN 41 =0 V
*
14
"""
80
'"
~
1:;
II
10
8.0
-
4.0
2.0
o
Ik
60
~
V
CT =0001 "F
,;'
6.0
:::>
0
>-
ffi
I--
~
10ltl
10k
~
~
~
40
"'-
""
160
1M
-180
~
20
"'"
o
o
lOOk
I0
20
"
35
30
DEAD-TIME CONTROL VOLTAGE (V)
FIGURE 7 - EMITTER FOLLOWER CONFIGURATION
OUTPUT-SATURATION VOLTAGE versus
EMITTER CURRENT
FIGURE 8 - COMMON EMITTER CONFIGURATION
OUTPUT-SATURATION VOLTAGE versus
EMITTER CURRENT
9
3
V~C
I. 8
i
140
I T e--e--
10. OSCILLATOR FREQUENCY (HZ)
~
-120
VCC=15 V
CT =0001 I-- I - RT =47 k
~
w
u
12
100
>
100 k
=
L-
I
I. 6
5
./
I-- ..-
I-I-- f--
I--
I--
0
V
9
8
3
7
-~
---
V
/"
V
V P
........
V
6
I. 2
I
T T
VCC=15V-
2
7
4
~
- 100 if~
100
Q
'"
10 k
" '"
111111
18
16
- '"
'"~
FIGURE 6 - PERCENT DUTY CYCLE versus
DEAD-TIME CONTROL VOLTAGE
20
0
~
I. fREQUENCY (Hli
FIGURE 5 - PERCENT DEAD-TIME versus
OSCILLATOR FREQUENCY
......
...
:l!
-80
0
""'-
RT. TIMING RESISTANCE Ilil
iii
-60
"'-...
~ 50
~
~ 40
t
~:-
20
I
VCC = 15V_
::'VO = 3 V
- 20
RL = 2k!l - 40
Or---...
O
j: t
+-
r-
.0, /.(F
10k
~
vcc
:jeT
~"i"
C, ~ o+-+~
t;
100
:-f:i t t FH
""h. ~1101""
100k
5
50
100
150
200
250
50
100
150
Ie COLLECTOR CURRENT (mA)
IE. EMInER CURRENT (mAl
281
200
250
~C34060,~C35060
FIGURE 9 - STANDBY-SUPPLY CURRENT
versus SUPPLY VOLTAGE
8.0
7.0
_
1
~ 5.0
r
1/
g:;
a
4. 0
i~
3. 0
.B
0
0
0
I
/
./
- ------
6.0
/
5.0
10
15
20
25
30
35
40
Vee. SUPPLY VOLTAGE IVI
FIGURE 11 -- DEAD-TIME AND FEEDBACK CONTROL
TEST CIRCUIT
FIGURE 10 - ERROR AMPLIFIER CHARACTERISTICS
Vee = 15 V ....._ _ _-,
L--o----~+
Error Amplifier
Under Test
Test
Inputs
t
150 l!
2W
Dead- Vee
T,me
Feedback
Feedback
Terminal
(Pm 3)
RT
e
eT
E
~"'--o Output
(+)
(-)
(+)
} '''0'
(-)
-=-
Ref
Out
50 kl!
Gnd
Other Error
Amplifier
FIGURE 13 - EMITTER-FOLLOWER CONFIGURATION
TEST CIRCUIT AND WAVEFORM
FIGURE 12 - COMMON-EMITTER CONFIGURATION
TEST CIRCUIT AND WAVEFORM
Output
TranSistor
Output
Transistor
282
MC34060, MC35060
FIGURE 14
~
ERROR AMPLIFIER SENSING TECHNIQUES
Va
To Output
Voltage of
System
POSITIVE OUTPUT VOLTAGE
VO= Vref (1
FIGURE 15
~
+
NEGATIVE OUTPUT VOLTAGE
Va
R,
R;)
FIGURE 16
DEAD-TIME CONTROL CIRCUIT
Output
Output
47 k
1
1
0001
Max%OnTlrne 92- (16:,)
1·R2
FIGURE 17 -- SLAVING TWO OR MORE
CONTROL CIRCUITS
Vref
Master
Slave
(Additional
Circuits)
283
~
To Output
Voltage of
System
SOFT-START CIRCUIT
~C34060,~C35060
FIGURE 18 - STEP-DOWN CONVERTER WITH SOFTSTART AND OUTPUT CURRENT LIMITING
Vin
~
8.0 t040 V
Vout
TIP 32
~--~------------T-------~----~~.
~~~~
50V/l0A
47
4.7 k
10
001
75
Vce
1
~t--
~+
9
C I-----'
2
+--A.,/\/'v--+---1 10M
3
~~~-4------~Comp
MC34060
14
50/50
L"
=-;:-:-1r--4------~ +
0.01[:;
~
MR850
13
+--+-----1 4.7 k
10/16V 4
?
0001
47k
150
6
*
+ 1\
4.7 k
5
47k
390
0.1
-TEST
CONDITIONS
- -- .
Line Regulation
VIC
~
8.0 V to 40 V, 10
~
RESULTS
lOA
25mV
05%,.
a mV
006%
--~-
Load Regulation
VIC
~
12 V, 10
~
1.0 mA to lOA
Output Ripple
VIC
~
12 V, 10
~
1.0 A
Short Circuit Current
VIC
~
12 V, RL
Efficiency
V ,n
~
12 V, 10
~
~
0.1
n
lOA
284
3
---
75 mV p-p PAR D
-
--------16 A
73%
---.----
1000
6.3 V
MC34060, MC35060
FIGURE 19 - STEP-UP CONVERTER
150~H
@4.0A
--
8.0 to 26 V
20~H@1.0A
=.
MR850
-t>r
Vou
28 VI
0.5 A
22 k
10
~
0.05
~t-
Vec
2
4.7 k
2.7 M
C
3
+
+
13
E
12
DT
4.7 k
300
8
~
470/35 V
~~
f,..TIPlll
7
Gnd '-------
Vref
4
+
-::
+
,-- -
3.9 k
9
Camp
MC34060
14
50/3 5 V:;:
-
CT
0.1
RT
6
5
470
0001
:;:
47 k
390
----------- ---1-------------.---.·-· --8.-.------.---.-. 1.L~n.-~-.R;.9.-~;;,-;-. 1 8-.0-.V-t~-i6V:~--=05-A 4~V
TEST
CONDITIONS
RESULTS
------- ---,- '- -------------'.o-n------ .-------VIC 0
-Load Regulation
I VIC 0 12 V, 10 = 1 0 mA to 0 5 A
-.........
----- -----------.----------------
------------- -----
--
-+--- ------ --- '----
VIC 0 12 V, 10 005 A
Output Ripple
E~fI:~e_~~~__
_
-- -'-,---- -,-------,--,-----
_
_
_J_Vlnce ~2_V,
IO-=05A
'Optional Circuit to minimize output ripple
285
_
_ _
____
-
0-.1.4%
0 18%
------
50 mV
~~V p-~f'!...f1..i-l _
1____~ ___
470/ 35 V
MC34060, MC35060
FIGURE 20 - STEP-UP/DOWN VOLTAGE INVERTING
CONVERTER WITH SOFT-START AND
CURRENT LIMITING
8.0 to 40 V
TIP 32C
.:t.L
MR851
.....
--
Vo ut
20 I'H •
-15 VI
0.2 SA
"
@ 1.0 A
47
30 k
10
~
0.01
~E-
2
7.5 k
1.0M
"
Comp
MC34060
14
0.01;4:::
C~
-
3
+
5015 OV
75
VCC
+
150 l'H
jj @2.0A
+
13
~ 330/16 V
+'"
E~
-
~ Vref
10 k
Gnd
Dr
Cr
5
10/16V 4
~
Rr
6
II
+1\
4.7 k
47 k
3.3 k~
0001
47 k
820
1.0
TEST
CONDITIONS
Line Regulation
Load Regulation
Output Ripple
=8.0 V to 40 V. 10 =250 rnA
Vin =12 V. 10 =1 rnA to 250 rnA
Vin = 12 V, 10 =250 rnA
Vin
Short CircUIt Current Vin = 12 V, RL = 0.1 !l
Efficiency
*
Optional
CirCUit
Vin
to
minimiZe
=12 V, 10 = 250 rnA
output ripple
286
RESULTS
52 mV
035%
47 mV
0.32%
10 mV p.p. PAR.D.
330 rnA
86%
.
:::1::::
+
33 0/16 V
FIGURE 21 ~ 33 WATT OFF-LINE FLYBACK CONVERTER
WITH SOFT-START AND PRIMARY POWER LIMITING
lN4003
lN5824
3:
Ll
50V/30A
3 each
00047 UL CSA
n
W
~
C)
~
lN4934
12 075 A
47/25 V
Common
22 k
10 35 V
10
VCC
-12/075 A
C~
lN4742T 180/200V
2.2 M
33 k
~_1C~~0~0~1__+-~3Icomp
7 5 k
115 Vac
14
. 20°0
T1
Coilcralt W2961
MC34060
T2
Core:
COllcralt 11-464-16, 0.025" gap
In each leg
8
13
'Optlonal R F I Filter
12
~Vrel
N
00
-...J
7
Gnd
DT
4
CT
Bobbin:
Collcralt 37-573
RT
200
Voutl Pout
15k
10
47
75 turns #26 Awg Bifilar wound
0001
47 k
Feedback:
15 turns #26 Awg
27k
10
11 k
lN4148
-
-
-
--
Secondary, 2 each:
14 turns #24 Awg Bifilar wound
Ll
CONDITIONS
RESULTS
Coilcralt Z7156, 15 JJH @ 5.0 A
---~~---
Line Regulation 5
aV
--------
Line Regulation ±12 V
- - - - - - - - , - - - - --Load Regulation 5
aV
VIn = 95 to 135 Vac. 10 = 3
aA
--~---------
Y,n = 95 to 135 Vac, 10 = ±O 75 A
-----------
Y,n
= 115 Vac,
10
20 mV
040%
---~~--~
52 mV
026%
.~--~-
=1 0
to 4 0 A
476 mV
95%
300 mV
2.5%
------~-
Load Regulation +12 V
Vin = 115 Vac, 10 = ±0.4 to ±0.9 A
---~--
t
L __
Secondary, 5.0 V:
6 turns #22 Awg Bifilar wound
27 k
-----_.-
TEST
--
Windings:
Primary, 2 each:
6
51
Output Ripple 5
aV
Vin = 115 Vac, 10 = 3
aA
Output Ripple +12 V
Vin = 115 Vac, 10 = ±O 75 A
Efficiency
Vin = 115 Vac, 10 5
aV= 3aA
10 ±12 = ±0.75 A
RD==J
45 mV POp PAR D
75 mV pop P A
74%
L2, L3
Coilcralt Z7157, 25 JJH @ 1.0 A
P
3:
n
W
UI
C)
~
C)
®
MC7800
Series
MOTOROLA
3-TERMINAL POSITIVE VOLTAGE REGULATORS
THREE-TERMINAL
POSITIVE FIXED
VOLTAGE REGULATORS
These voltage regulators are monolithic integrated circuits designed as fixed-voltage regulators for a wide variety of applications
including local. on-card regulation. These regulators employ internal
current limiting, thermal shutdown, and safe-area compensation.
With adequate heatsinking they can deliver output currents in excess
of 1.0 ampere. Although designed primarily as a fixed voltage regulator, these devices can be used with external components to obtain
adjustable voltages and currents.
•
•
•
•
•
•
Output Current in Excess of 1.0 Ampere
No External Components Required
Internal Thermal Overload Protection
Internal Short-Circuit Current Limiting
Output Transistor Safe-Area Compensation
Output Voltage Offered in 2% and 4% Tolerance
K SUFFIX
METAL PACKAGE
CASE 1
(Bottom View)
(TO-3 TYPE)
SCHEMATIC DIAGRAM
,---~-----------,----------~----~--,-------,--olnput
T SUFFIX
PLASTIC PACKAGE
10 k
CASE 221A
lOOk
500
TO-220 TYPE
1
Pin 1. Input
2
2. Ground
3. Output
0.3
.....--{) Output
1-1-------j~~-----+---r--
STANDARD APPLICATION
ln p u t $ C 7 8 X X Output
C
•
o 1~3}.J.F
Co··
0-19k
2.7 k
A common ground
required between the
Pin 2 is ground
for Case 221 A.
put voltage even dunng the low pomt on the
input ripple voltage.
Case is ground
500
for Case 1.
XX "" these two digits of the type number mdi·
cate voltage.
*
ORDERING INFORMATION
Device
IS
Input and the output voltages. The Input voltage must remain typically 2.0 V above the out-
5k
Output Voltage
Tolerance
Temperature Range
to +150 oC
MC78XXK
MC78XXAK
4%
2%
~55
MC78XXBK
4%
-40 to +125°C
MC78XXCK
MC78XXACK
4%
2%
o to +125°C
MC78XXCT
MC78XXACT
4%
2%
MC78XXBT
4%
Package
= Cin
IS required if regulator IS located an
appreciable distance from power supply
filter.
** = Co is not needed for stability; however,
it does improve transient response.
xx indIcates nomInal vOltage
Metal Power
TYPE NO /VOLTAGE
Plastic Power
-40 to +125°C
288
15 Volts
MC7805
5.0 Volts
MC7815
MC7806
6.0 Volts
MC7818
18 Volts
MC7808
8.0 Volts
MC7824
24 Volts
MC7812
12 Volts
MC7800 Series
MC7800 Series MAXIMUM RATINGS (TA = +25°C unless otherwise noted)
Symbol
Value
Unit
Vin
35
40
Vdc
PD
1/8JA
8JA
Internally Limited
15.4
65
Watts
mW/oC
°C/W
TC = +25°C
Derate above TC = +95°C (See Figure 1)
Thermal Resistance, Junction to Case
PD
1/8JC
8JC
Internally Limited
200
50
Watts
mW/OC
°C/W
TC~+25°C
Derate above TA :::: +25°C
Thermal Resistance, Junction to Air
PD
1/0JA
8JA
Internally limited
22.5
45
mW/oC
°C/W
TC=+25°C
Derate above Te::::: +65°C (See Figure 2)
Thermal Resistance, Junction to Case
PD
1/8JC
8JC
Internally Limited
182
55
mW/OC
Tstg
-65 to +150
°c
Rating
Input Voltage (5.0 V - 18 V)
(24 V)
Power DIssipation and Thermal Characteristics
Plastic Package
TA ~ +25°C
Derate above TA = +25°C
Thermal Resistance, Junction to Air
Storage Junction Temperature Range
Operating Junction Temperature Range
Watts
°c/W
--
--
°C
TJ
--
Watts
-55 to +150
to +150
-40 to +150
MC7800, A
MC7800C, AC
MC7800, B
o
--~~~.-
DEFINITIONS
QUiescent Current - That part of the Input current that
delivered to the load.
Line Regulation - The change In output voltage for a change In
the Input voltage The measurement IS made under conditions of
low dissipation or by uSing pulse techniques such that the average chip temperature IS not significantly affected.
Load Regulation - The change In output voltage for a change
load current at constant chip temperature.
IS
not
Output NOise Voltage - The rms ac voltage at the output. W1tll
constant load and no Input ripple, measured over a specIfied frequency range
In
Long Term Stability - Output voltage stability under accelerated
life test conditlons with the maximum rated voltage listed In
the deVices' electnca I characteristics a nd maxim um power
dissipation
MaXimum Power DIssipation - The maximum total deVice dlSSI~
pation for which the regulator will operate within specificatIOns.
289
MC7800 Series
MC7805. B. C
I 1] un ess 0 Iherwise noled)
ELECTRICAL CHARACTERISTICS (Vin= 10 V·0=
I
500 m A T
J= T
lowl0 Thiah IN oe
MC7806
MC78068
Characteristic
Symbol
Min
Typ
Max
Min
Typ
Max
Output Voltage ITJ
=+25°C}
Vo
Output Voltage
4.8
5.0
5.2
4.8
5.0
5.2
4.8
5.0
-
4.75
5.0
5.25
-
Ragin
Load Regulation ITJ =+25 0 C, Note 2)
5.0 mA';; 10';; 1.5 A
250 mA,;; 10';; 750 mA
Reg'oad
QUiescent Current (TJ
=+25°C)
18
Quiescent Current Change
7.0 Vdc~ Vin -s;;; 25 Vdc
8.0 Vdc~ V tn ~ 25 Vdc
50 mA,," 10';; 1.0 A
~IB
Ripple Rejection
B OVde';; Yin';; 18 Vde. 1= 120 Hz
RR
Dropout Voltage (10 = 1.0 A. TJ = +2S°C)
Output NOise Voltage (TA
10 Hz';; I';; 100 kHz
=+25°C)
Output ReSistance f = 10kHz
Short-CirCUit Current Limit (TA
Vin = 35 Vdc
Peak Output Current ITJ
=+25°C)
=+25°C)
Average Temperature CoeffiCient of
Output Voltage
-
-
-
-
-
4.65
5.0
5.35
4.75
5.0
5.25
-
-
-
2.0
1.0
50
25
-
7.0
2.0
100
50
-
7.0
2.0
100
50
-
25
8.0
100
25
-
40
15
100
50
-
40
15
100
50
-
3.2
6.0
-
4.3
8.0
-
4.3
8.0
-
-
-
-
-
0.8
0.5
-
-
0.3
0.04
-
--
-
1.3
-
-
68
75
-
-
1.3
0.5
-
68
-
-
2.0
25
-
2.0
-
10
40
-
10
-
-
RO
-
17
-
-
17
Ise
-
02
1.2
-
0.2
-
-
25
3.3
-
2.2
±0.6
-
-
-1.1
-
13
'max
TCVO
Vo
-
Vdc~
-
-
05
68
-
20
-
10
dB
Vdc
"VI
Vo
17
-
mU
02
-
A
-
22
-
A
-
-1 1
-
mVI
'c
MC7805AC
Typ
Max
4.9
5.0
51
49
50
51
48
50
5.2
48
50
52
-
2.0
3.0
1.0
2.0
10
10
40
10
-
70
10
20
70
50
50
25
50
25
50
-
-
-
25
25
80
100
100
50
-
43
6.0
60
-
-
Unit
Vde
Vde
20 Vdc
--
lme Regulation (Note 2)
75
80
80
73
-
-
Vo
~
-
-
Output Voltage
(50 mA';; 10';; lOA. PO';; 15 WI
mA
mA
Vo
Output Voltage (TJ = +25°C)
Vde
mV
Vn
Vin -
Unit
mV
MC7805A. AC
ELECTRICAL CHARACTERISTICS (V10- 10 V IO- lOA TJ-- Tlow to Thloh [Note 1J unless otherWise noted)
MC7805A
Symbol
Characteristics
Max
Min
Typ
Min
Vm
5.2
Vde
Line Regulation (TJ = +25°C. Note 2)
7.0 Vdc~ V ln ~ 25 Vdc
8.0 Vde';; Vin';; 12 Vde
~
MC7805C
Typ
Max
Vo
(5.0 mA,;; 10';; 1.0A. PO';; 15 W)
7.0 Vdc ~ Vin ~ 20 Vdc
8.0 v .... e ~ V ln ~ 20 Vdc
75 Vdc
Min
V m :::;;; 25
Vdc~ V'"~ 12
Vdc~ V m ::::; 12
Vdc ~ Vm ~ 20
Reg ln
Vdc, '0 = 500 rnA
Vdc
Vdc, TJ= +25°C
Vdc, TJ =+25°C
Load Regulation (Note 2)
SOmA';; 10';; 1 5 A
SOmA,," 10';; 1.0 A
50 mA';; 10';; 1.5 A. TJ = +25'C
250 rnA ~ 10 :::;;; 750 rnA
QUiescent Current
TJ =+25°C
QUiescent Current Change
8 0 Vdc :( Vm ::;;;: 25 Vdc, 10
75 Vdc ~ Vm ~ 20 Vdc, TJ
-
-
Dropout Voltage (10 = 1.0 A. TJ
=+25°C)
-
-
-
-
80
25
-
.-
32
50
40
-
0.3
0.2
004
0.5
0.5
0.2
-
-
~IB
-
-
08
08
05
dB
RR
Vin -
mA
mA
-
5 0 mA';; 10 ,;; 1.0 A
Ripple Rejection
80 Vdc S;;;; V In :::;;; 18 Vdc, f = 120 Hz,
TJ =+25°C
80 Vdc:S;;; Vm ~ 18 Vdc, f= 120 Hz,
10 = 500 mA
mV
Regload
IB
=500 rnA
=+25°C
mV
Vo
68
75
-
-
-
68
75
-
-
68
-
-
2.0
2.5
-
2.0
-
Vde
40
-
10
-
"VIVO
-
Output NOise Voltage (TA = +25°C)
10 Hz';; I';; 100 kHz
Vn
-
10
Output ReSistance (f = 1.0 kHz)
RO
-
-
17
-
mil
Ise
-
17
Short-CirCUit Current Limit (TA = +25°C)
Vm = 35 Vde
'
0.2
1.2
-
0.2
-
A
2.5
3.3
-
2.2
-
A
±0.6
-
-
-1.1
-
mV/oC
Peak Output Current (TJ = +25°C)
Imax
1.3
Average Temperature CoeffiCient of Output Voltage
TCVO
-
NOTES:
Tlow = -55°C lor MC78XX. A
= 0' lor MC78XXC. AC
= -40°C for MC78XXB
2. Load and line regulation are specified at constant Junction temperature. Changes in Va due to heating effects must be taken into account
separately. Pulse testmg with low duty cycle is used.
290
MC7800 Series
MC7806, B, C
ELECTRICAL CHARACTERISTICS (Vin -- 11 V IO-- 500 mA TJ -- Tlow to Thi h [Note 1] unless otherwise noted)
Characteristic
Symbol
Output Voltage (TJ::: +25°C)
Vo
Output Voltage
{5.0 mA,. 10 ,. 1.0 A, Po ,. 15 WI
Vo
Min
MC7806
Typ
Max
Min
5.75
6.0
6.25
5.75
-
-
Line Regulation (TJ::: +25 D C, Note 2)
Min
6.25
575
6.0
6.25
-
-
57
60
63
-
-
6.0
MC7806C
Typ
Max
-
5.65
6.0
6.35
57
6.0
6.3
-
-
30
2.0
60
30
-
90
3.0
120
60
-
9 0 Vdc~ VIO~ 13 Vdc
Load RegulatIOn (TJ::: +25°C, Note 2)
5.0 mA,. 10" 1.5 A
250 mA,. 10" 750 mA
-
-
27
9,0
100
30
43
16
120
60
32
60
-
4.3
80
-
-
-
03
004
08
05
-
-
13
05
65
73
-
-
65
90
30
120
60
.-
43
16
120
60
-
43
8.0
mV
Regload
QUiescent Current (TJ ::: +25°C)
IS
Quiescent Current Change
80 Vdc ~ V ln ::;;; 25 Vdc
-
90 Vdc e:;;; V ln ::;;; 25 Vdc
5.0 mA,. 10" 1.0 A
RR
mA
mA
:>IS
Ripple Rejection
Vde
mV
Regin
B.O Vdc ~ Vin::;;; 25 Vdc
Unit
Vde
-
8.0 Vdc::;;; Vin::;;; 21 Vdc
9.0 Vdc::;;; Vin::;;; 21 Vdc
MC7806B
Typ
Max
-
-
13
-
-
-
-
-
65
-
20
-
10
-
-
05
-----dS
90 Vdc::;;; Vm ::;;; 19 Vdc, f::: 120 Hz
Vin - Vo
-
2.0
25
-
20
Output NOise Voltage (TA = +25°C)
10 Hz::;;; f~ 100 kHz
Vn
-
10
40
-
10
-
Output ReSistance f::: 10kHz
RO
17
-
-
17
-
Short-Circuit Current Limit (TA::: +25°C)
Ise
-
02
12
-
0.2
-
Dropout Voltage (10 ::: lOA, TJ::: +25°C)
-
MVI
17
-
mll
02
-
Vo
----
-
Vin ::: 35 Vdc
Peak Output Current (TJ = +25°C)
Imax
Average Temperature Coefficient of
Output Voltage
MC7806A, AC
ELECTRICAL CHARACTERISTICS (V
Characteristics
Output Voltage (TJ
TCVO
13
-
2.5
33
±O.7
-
-
22
-
-
22
-
-
-08
=+25°C)
Vo
Output Voltage
(50 mA,. 10" 1 0 A. PO,. 15 WI
~~6 Vdc ~ V in ~ 21 Vdc
588
60
612
588
576
60
624
576
Load Regulation (Note 2)
5 0 mA :;;; 10 =;:;: 1 5 A
5 0 mA ~ 10 =;:;: 1 0 A
50 mA ~ 10 ~ 1 5 A. TJ
250 mA ~ 10';:;; 750 mA
11
15
50
11
-
-
30
50
20
40
-
27
50
-
f------
Max
612
60
624
[ - - - - - - - f-------
-
QUiescent Current Change
90 Vdc';:;; Vm =;:;: 25 Vdc, 10
8 6 Vdc~ V tn =;:;: 21 Vdc, TJ
5.0 mA =;:;: 10 ~ lOA
-
-
90
11
30
9~
f--
60
60
30
60
Ripple Rejection
90 Vdc =;:;: V in =;:;: 19 Vdc, f
TJ =+25°C
9.0 Vdc ~ Vln ~ 19 Vdc, f
100500 mA
-
-
-
-
90
25
-
-
_.
mV
43
43
16
100
100
50
43
60
60
-
-
08
08
0.5
-
-
-
-
-
-
65
-
20
-
Vde
10
-
MV/VO
17
-
mfl
-
32
50
4.0
-
0.3
02
004
0.5
05
02
73
-
mA
mA
:>18
=500 rnA
=+25°C
-.~-------'"
mV
-
IS
Vde
Vde
-
=+25°C
Unit
~-------.
60
Regload
QUiescent Current
-
d8
RR
= 120 Hz,
65
= 120 Hz,
= lOA, TJ =+25°C)
Output NOise Voltage (TA =+25°C)
Dropout Voltage (10
Hz~ f~
--~-
MC7806AC
Typ
Reg ln
~~5°C
10
mVI
°C
Vo
-~
Line Regulation (Note 2)
86 Vdc ~ V ln ~ 25 Vdc, 100500 mA
90 Vdc ~ V ln ~ 13 Vdc
90 Vdc < V In ';::;; '3 Vdc. TJ = +25°C
83 Vdc ~ Vin ~ 21 Vdc, TJ =+25°C
A
-
- - - _..
- - ----
'"
A
--
-08
0 11 V I 0 10 AT J 0 low t 0 Thigh [N 0 te 1] u nless otherWise noted)
0
MC7806A
Symbol
Min
Typ
Max
Min
Vde
Yin - Vo
Vn
65
73
-
2,0
2.5
10
40
100 kHz
Output ReSistance (f = 1.0 kHz)
Short-Circuit Current Limit (TA
Vln = 35 Vdc
Peak Output Current (TJ
RO
=+25°C)
=+25°q
Average Temperature Coefficient of Output Voltage
Ise
'max
TCVO
1.3
-
17
-
0.2
12
2.5
3.3
-
2,2
-
-
-0.8
±O.7
-
02
-
Thigh - +150°C for MC78XX, A
NOTES' 1. Tlow 0 -55'C for MC78XX, A
o +125'C for MC78XXC, AC. 8
o 0' for MC78XXC. AC
o -40'C for MC78XXS
2. Load and line regulation are specified at constant junction temperature. Changes in Vo due to heating effects must be taken into account
separately_ Pulse testtng with low duty cycle is used.
291
A
A
mV/oC
MC7800 Series
MC7808. B. C
ELECTRICAL CHARACTERISTICS (Vin - 14 V 10 - 500 rnA TJ-- Tlow to Thioh [Note 1] unless otherwise noted)
Characteristic
Symbol
Output Voltage (TJ = +25°C)
Vo
Output Voltage
Vo
(5.0 rnA"; 10"; 1.0A, PO"; 15 WI
10.5 Vdc ~ Vin ~ 23 Vdc
11.b Vdc ~ Vin ~ 23 Vdc
Line Regulation (TJ =+25°C. Note 2)
10.5 Vdc ~ Vin ~ 25 Vdc
11 Vdc ~ Vin ~ 17 Vdc
Regin
Load Regulation (TJ = +25°C, Note 2)
5.0 mA~ 'a ~ 1.5 A
250 mA ,,; 10 ,,; 750 rnA
Reg'oad
QUiescent Current {TJ::: +25°C)
7.7
B.O
-
-
7.6
RR
Vin -
8.0
8.3
7.7
8.0
8.3
Vde
-
-
-
-
7.6
8.0
8.4
8.0
8.4
7.6
8.0
8.4
-
-
-
-
3.0
2.0
80
40
-
12
5.0
160
80
-
12
5.0
160
80
-
28
9.0
100
40
45
16
160
80
160
80
3.2
6.0
4.3
8.0
-
45
16
-
-
4.3
8.0
-
-
-
-
-
10
1.0
05
-
-
-
-
05
62
-
-
62
-
2.0
-
-
2.0
-
10
-
-
-
18
-
mll
0.2
-
A
-
-
22
-08
-
rnV
mA
mA
0.3
0.04
0.8
0.5
62
70
-
-
2.0
2.5
10
40
Vo
Output NOise Voltage (TA:: +25°C)
10 Hz~ f~ 100 kHz
Vn
Output Resistance f :: 1 .0 kHz
RO
Short-CircUit Current Limit (TA::: +25°C)
Ise
:::
Unit
7.7
-
-
-
.-~
dB
21.5 Vdc, f = 120 Hz
Dropout Voltage (IO::: 1.0 A, TJ;;: +25°C)
V In
MC7BOBC
Typ
Max
.lIS
Ripple Rejection
~
Min
mV
10.5 Vdc ~ Vin ~ 25 Vdc
11.5 Vdc~ V'"~ 25 Vdc
5.0 mA,,; 10"; 1.0 A
11 5 Vdc:S; Vin
8.3
MC7BOBB
Typ
Max
Min
Vde
IS
QUiescent Current Change
MC7BOB
Typ
.Max
Min
-
-
10
0.2
1.2
-
25
3.3
-
22
±1.0
-
-
-O.B
lB
-
18
0.2
Vde
"VI
Vo
35 Vdc
Peak Output Current (TJ ::: +25°C)
Imax
Average Temperature Coefficient of
Output Voltage
TeVO
MC7BOBA, AC
ELECTRICAL CHARACTERISTICS (V In ::: 14V IO~ lOA TJ
Symbol
Characteristics
Output Voltage (TJ :: +25°C)
Vo
Output Voltage
(50 mA,,; 10"; 1 0 A, PO'" 15 WI
10 6 Vdc:S; V ln ~ 23 Vdc
Vo
13
-
~
low t 0 Thigh IN ot e 1J u nl e ss
0
A
mV/
°e
th erwi e no t edl
--
Min
MC7808A
Typ
Max
Min
MC7808AC
Typ
Max
7.84
8.0
816
784
80
816
77
80
8 3
77
80
83
-
4.0
6.0
20
4.0
13
20
60
13
12
15
50
12
80
80
40
80
-
28
50
-
-
-
-
-
90
25
100
100
50
-
50
40
-
3.2
-
45
45
16
60
60
0.3
0.2
004
05
05
02
-
Unit
-Vdc
Vde
---~-
Line Regulation (Note 2)
10.6 Vdc ~ Vln ~ 25 Vdc, 10 ::: 500 mA
11 Vdc:S:;; VIO:S; 17 Vdc
11 Vdc:S; Vln:S; 17 Vdc, TJ ::: +25°C
104 Vdc ~ VIO:S; 23 Vdc, TJ ::: +25°C
Load Regulation (Note 2)
50 mA ~ 10:S; 1.5 A
5.0mA:S;10:S;1.0A
5.0 mA~ 10:S; 1.5ATJ:::+25°C
250 mA:S; IO:S; 750 rnA
QUiescent Current
TJ::: +25°C
Reg ln
mV
-
-
-
mV
Regload
IS
QUiescent Current Change
11 Vdc:S:;; VIO:S; 25 Vdc, 10 ::: 500 mA
106 Vdc:S; VIO:S:;; 23 Vdc, TJ::: +25°C
5 0 mA ,,; 10 ,,; 1.0 A
.lIB
Ripple RejectIOn
11 5 Vdc~ Vln:S:;; 21.5 Vdc, f= 120 Hz,
TJ::: +25°C
11.5 Vdc:S:;; VIO:S:;; 21.5 Vdc, f::: 120 Hz,
10 ~ 500 mA
RR
Dropout Voltage (10::: 1.0 A, TJ::: +25°C)
-
43
-
mA
mA
--
--
-
08
08
05
dB
62
70
-
-
-
-
62
70
-
-
62
-
"VIVO
V ln - Va
-
20
25
Output NOise Voltage (TA::: +25°C)
10 Hz"; f,,; 100 kHz
Vn
-
10
40
Output ReSistance (f::: 1.0 kHz)
RO
-
Ise
-
18
Short-Circuit Current limit (TA::: +25°C)
Vin::: 35 Vdc
0.2
12
2.5
3.3
±1.0
-
Peak Output Current (TJ::: +25°C)
Imax
1.3
Average Temperature Coefficient of Output Voltage
TCVO
-
-
2.0
10
18
-
mil
02
-
A
2.2
-
A
-08
-
mV/oC
NOTES: 1. Tlow = -55°C for MC78XX, A
=0° for MC78XXe, AC
= -400 e for MC78XXS
2. Load and line regulation are specified at constant junction temperature. Changes in Vo due to heating effects must be taken Into account
separately. Pulse testing with low duty cycle is used.
292
Vde
MC7800 Series
MC7812, 8, C
ELECTRICAL CHARACTERISTICS IVIn-- 19 V , IO-- 500 rnA TJ-- T low to Thigh [Note 1] u nless otherWIS e n 0 ted I
Characteristic
Symbol
Output Voltage (TJ:::; +25°C)
Vo
Output Voltage
Vo
150 rnA,;; 10';; lOA. PO';; 15
14 5 Vdc~ Vln~ 27 Vdc
15 5 Vdc";:; V ln ~ 27 Vdc
Min
MC7812
Typ
Max
Min
11.5
12
12.5
11.5
-
-
11.4
-
-
50
30
120
60
-
30
10
120
60
-
34
60
-
-
-
-
-
03
004
08
05
61
68
-
Vin - Vo
-
20
25
Vn
-
10
Output Resistance f = 10kHz
RO
18
Short-Clfcult Current Limit (T A:: +25°C)
Vin = 35 Vdc
Isc
-
02
13
25
QUIescent Current (TJ - +25°C)
16
QUiescent Current Change
12.5
Unit
Vdc
-
114
12
126
12
126
-
-
-
13
60
240
120
-
13
60
240
120
46
17
240
120
46
17
240
120
44
80
-
4.4
80
1.0
rnV
-
rnV
mA
:'16
14 5 Vdc~ Vin ~ 30 Vdc
15 Vdc :::;; Vin ~ 30 Vdc
5,0 rnA ~ 10 ,,;;; 1 ~O A
RR
Ripple Rejection
rnA
-
-
-
-
05
60
-
dB
-
-
-
60
-
-
-
20
-
-
20
40
-
10
-
"VI
-
-
18
-
18
-
rnil
1,2
-
02
-
02
-
A
33
-
22
-
22
-
A
-
-1 0
-
mVI
-
10
05
-
25 Vdc, f = 120 Hz
Dropout Voltage (10 = lOA TJ
Output NOise Voltage (TA
10 Hz:;;;; f:S; 100kHz
=+25°C)
= +25°C)
Peak Output Current (TJ ::: +25°C)
Average Temperature Coefficient of
Output Voltage
10
Imax
TCVO
±15
-
-
-
-1 0
'C
Output Voltage (TJ::: +25°C)
Vo
Output Voltage
(5 0 rnA';; 10';; lOA, Po ,;; 1 5 WI
148 Vdc oS; Vin oS; 27 Vdc
Va
Line Regulation (Note 2)
14 8 Vdc oS; VI noS; 30 Vdc, 100500 rnA
16 Vdc oS; Vln oS; 22 Vdc
16 Vdc oS; Vln oS; 22 Vdc, TJ ::: +25°C
145 Vdc ~ Vln ~ 27 Vdc, TJ::: +25°C
Load Regulation (Note 2)
5 0 mA s:: 10 ~ 1 5 A
50 mA oS; 10 ~ lOA
50 mA ~ 10 ~ 1 5 A, TJ::: +25°C
250 mA...s; 10 ~ 750 mA
QUiescent Current
TJ::: +25°C
MC7812AC
Typ
Max
1175
12
1225
11 75
12
1225
11 5
12
125
115
12
125
-
50
80
30
5.0
18
30
9.0
18
13
16
60
13
120
120
60
120
-
30
50
-
-
-
mV
Regload
-
Ripple Rejection
15 Vdc ~ Vin ~ 25 Vdc, f ::: 120 Hz,
TJ::: +25°C
15 Vdc ~ Vin ~ 25 Vdc, f::: 120 Hz,
10 =500 rnA
RR
10
25
-
-
100
100
50
-
34
50
40
-
0:
0.2
004
05
0.5
02
-
-
61
68
-
-
-
-
-~
-
46
46
17
-
44
60
60
0.8
08
0.5
rnA
rnA
-
Vln - Vo
-
-
-
-
:,IB
Vdc
rnV
-
16
Unit
Vdc
Reg m
QUiescent Current Change
15 Vdc ~ Vin ~ 30 Vdc, 10 ::: 500 mA
148 Vdc ~ Vm ~ 27 Vdc, TJ::: +25°C
5 0 rnA ~ 10 ~ lOA
Dropout Voltage (10::: 1 0 A, TJ ::: +25°C)
Vdc
Vo
-
MC7812A, AC
ELECTRICAL CHARACTERISTICS (V In - 19 V IO-- lOA TJ-- Tlow to Thigh [Note 11 unless otherwise noted I
MC7812A
Characteristics
Symbol
Min
Typ
Max
Min
d6
61
68
-
-
2.0
2.5
10
40
Output NOise Voltage (TA::: +25°C)
10 Hz";; f";; 100 kHz
Vn
Output Resistance (f::: '.0 kHz)
RO
Short-Circuit Current Limit (TA::: +25°C)
Vin ::: 35 Vdc
Ise
-
Peak Output Current (TJ::: +25°C)
Imax
1.3
Average Temperature Coefficient of Output Voltage
TCVO
-
NOTES'
12
Regload
5.0 rnA';; 10';; 1 5 A
250 mA~ 10::;; 750 mA
~
11.5
Reg m
-
Load Regulation (TJ - +25°C. Note 2)
-
114
-
Note 2)
145 Vdc ~ VIn ~ 30 Vdc
, 6 Vdc ~ V In :;::; 22 Vdc
15 Vdc:::;; V ln
125
MC7812C
Typ
Max
Vdc
12.6
=+25°C,
12
Min
WI
12
Line RegulatIOn (TJ
MC7812B
Typ
Max
-
60
2.0
10
18
--
-
18
0.2
1.2
-
0.2
2.5
3.3
-
2.2
-
-
-1.0
±1.5
-
-
Tlow 0 -55°C for MC78XX. A
Thigh = +150 oC for MC78XX, A
::: 0° for MC78XXC, AC
= +125°C for MC78XXC. AC, B
o -40°C for MC78XXB
Load and line regulation are specified at constant junction temperature. Changes In Vo due to heating effects must be taken IOta account
separately, Pulse testing with low duty cycle is used.
293
Vdc
"VIVO
mfl
A
A
mV/oC
MC1800 Series
MC7815. B. C
ELECTRICAL CHARACTERISTICS IVin - 23 V IO-- 500 rnA TJ-- TI ow to Thiah [Note 1) unless otherwise noted)
MC7815
MC7815B
Symbol
Characteristic
Min
Typ
Max
Min
Max
Typ
Output Voltage (TJ::; +25°C)
Vo
Output Voltage
Vo
14.4
-
-
Regin
Load Regulation (TJ::; +25°C, Note 2)
5.0 mA.::;;; IO~ 1,5 A
250 rnA';; 10';; 750 rnA
Regload
la
QUIescent Current Change
17.5 Vdc ~ Vin ~ 30 Vdc
185 Vdc:S; Vin ~ 30 Vdc
5 0 rnA,;; 10 ,;; 1.0 A
.lla
Ripple Rejection
18.5 Vdc:::; VIn:S;: 28.5 Vdc, f:::; 120 Hz
RR
Vin -
Vo
Vn
Output ReSIstance f = 1,0 kHz
RO
Short-Circuit Current limit (TA::; +25°C)
Vin::: 35 Vdc
Ise
-
6.0
3.0
150
75
-
32
10
150
75
-
3.4
6.0
-
-
08
0.5
60
66
-
-
2.0
2.5
10
40
-
19
13
-
-
02
12
2.5
3.3
±18
-
Symbol
Output Voltage (TJ = +25°C)
Vo
Output Voltage
(5.0 mA,;; 10';; lOA. PO';; 15 WI
17 9 Vdc :(: Vin :(: 30 Vdc
Vo
la
.lla
Ripple Rejection
18.5 Vdc:S: VIn:S: 28.5 Vdc, f = 120 Hz,
TJ = +25°C
185 Vdc:s: VIn:s: 28 5 Vdc, f = 120 Hz.
10= 500 rnA
RR
=1.0 kHz)
Short-CircUit Current Limit (TA = +25°C)
Vin = 35 Vdc
Peak Output Current (TJ
=+25°C)
Average Temperature Coefficient of Output Voltage
NOTES:
-
15
15.75
Vde
15
15.75
-
-
-
13
6.0
300
150
-
13
6.0
300
150
-
52
20
300
150
-
-
52
20
300
150
44
8.0
--
4.4
8.0
-
-
-
0.5
58
-
-
1.0
10
0.5
58
-
da
-
20
-
-
2.0
10
-
"VI
-
19
-
19
02
-
-
02
-
2.2
-
-
22
-10
-
-
-1 0
14.25
-
-
rnA
-
10
-
11 u nless otherw ,se
Vde
mll
A
A
mVI
noted)
Min
MC7815A
Typ
Max
Min
MC781SAC
Typ
Max
14.7
15
153
14.7
15
153
14.4
15
156
144
15
156
-
6.0
60
3.0
6.0
22
22
10
22
-
32
50
Unit
Vdc
Vdc
mV
-
13
16
60
13
-
52
52
20
100
100
50
-
60
60
-
-
150
150
75
150
-
-
-
-
-
-
10
25
3.4
55
45
-
44
0.5
05
02
-
-
-
-
-
0.3
0.2
004
-
-
08
08
0.5
60
66
-
-
-
-
-
58
20
-
10
-
"VIVO
RO
Ise
rnA
mA
-
Vn
~
-
-
Vin _. Va
..
mV
Regload
QUiescent Current Change
17 5 Vdc:(: V ln :(: 30 Vdc, 10 = 500 mA
175 Vdc < Vln < 30 Vdc, TJ = +25°C
5.0 mA < 10 ~ 1.0 A
Output ReSistance (f
14.25
Unit
-
«
=+25°C)
-
Reg ln
«
Output NOise Voltage (TA
10 Hz:s: f~ 100 kHz
15.6
°C
MC7815A. AC
ElECTRICAL CHARACTERISTICS (V In = 23 V I0= lOA TJ= T low to T high [Note
~~pout Voltage (10 = 1.0 A, TJ = +25°C)
15
Vo
Imax
QUiescent Current
TJ = +25°C
MC7815C
Typ
Max
Min
14.4
rnA
0.3
0.04
TCVO
Load Regulatron (Note 2)
50 rnA';; 10';; 15 A
50 mA < 10 < lOA
50 mA
10 ~ 1 5 A, TJ = +25°C
250 rnA';; 10';; 750 rnA
15.6
mV
Peak Output Current (TJ = +25°C)
Line Regulation (Note 2)
179 Vdc:(: V ln :(: 30 Vdc, 10 = 500 mA
20 Vdc
Vin ~ 26 Vdc
20 Vdc ~ Vin ~ 26 Vdc, TJ = +25°C
17.5 Vdc ~ Yin ~ 30 Vdc, TJ = +25°C
15
mV
Average Temperature Coefficient of
Output Voltage
Characteristics
14.4
-
15.75
-
Output NOise Voltage (TA::; +25°C)
10Hz ~ f ~ 100 kHz
-
15
14.25
Line RegulatIon (TJ::; +25°C, Note 2)
175 Vdc ~ V ln :::;;; 30 Vdc
20 Vdc ::;;; Vm ~ 26 Vdc
Dropout Voltage (10::; 1.0 A, TJ::; +25°C)
15.6
Vde
(5.0 rnA';; 10';; 1.0 A. PO';; 15 WI
17.5 Vdc ~ Vin ~ 30 Vdc
18.5 Vdc ~ Vin ~ 30 Vdc
Quiescent Current (TJ:::; +25 Q C)
15
dB
60
66
-
-
2.0
2.5
10
40
-
Imax
1.3
TCVO
-
19
-
0.2
1.2
2.5
3.3
±1.8
-
-
19
-
m!l
0.2
-
A
-
2.2
-
A
-1.0
-
mY/DC
Th,gh - +1 50'C for MC78XX. A
Tlow = -55'C for MC78XX. A
. =+1 25'C for MC78XXC. AC. a
=0' for MC78XXC. AC
= -40'C for MC78XXa
2. Load and line regulation are specified at constant junction temperature. Changes In Vo due to heating effects must be taken into account
separately. Pulse testing with low duty cycle is used.
294
v~
MC7800 Series
MC7818. B. C
ELECTRICAL CHARACTERISTICS IV in - 27 V IO-- 500 rnA TJ-- Tlow to Thj~h [Note 1) unless otherwise noted)
Characteristic
Symbol
Output Voltage (TJ::: +25°C)
Va
Output Voltage
Va
150 rnA,; 10'; lOA, Po'; 15 W)
21 Vdc ~ V In ";; 33 Vdc
22 Vdc ~ Vin ~ 33 Vdc
Line Regulation (TJ::: +25°C, Note 2)
QUiescent Current (TJ':= +25°C)
QUiescent Current Change
21 Vdc ~ Vm -s;;; 33 Vdc
22 Vdc";; Vin ~ 33 Vdc
50 rnA'; '0'; 1.0A
Ripple RejectIon
22 Vdc ~ V In :::;; 32 Vdc, f::: 120 Hz
Dropout Voltage (10::: , 0 A, TJ -= +25°C)
MC7818C
Max
Min
Typ
Max
Min
Typ
Max
17.3
18
18.7
17.3
18
18.7
17.3
18
18.7
RR
V ln ~ Vo
Vn
Output ReSistance f::: 10kHz
RO
Short-Circuit Current Limit (T A::: +25°C)
'se
Vde
-
-
-
-
-
17.1
18
171
18
18.9
17.1
18
18.9
-
-
18.9
-
-
70
40
180
90
-
25
10
360
180
-
25
10
360
180
-
35
12
180
90
55
22
360
180
-
55
22
360
180
3.5
6.0
-
4.5
80
45
8.0
-
08
0.5
-
-
10
0.5
--
05
59
65
-
-
57
-
-
1.0
03
0.04
57
-
-
2.0
25
-
2.0
Vde
-
10
-
_.
40
-
20
10
10
-
"VI
-
19
-
19
19
02
-
0.2
-
rnil
12
-
--
0.2
-
25
3.3
-
22
-
A
-
-
-10
-
22
±2.3
-
-1 0
-
mVI
rnV
rnV
Regload
'8
.l18
Unit
Vde
Regin
Output Noise Voltage (T A::: +25°C)
10 Hz~ f~ 100 kHz
Vin ::: 35 Vdc
MC78188
Typ
-
21 Vdc ~ Vm ~ 33 Vdc
24 Vdc:S; Vin -::;;: 30 Vdc
Load Regulation (TJ::: +25°C, Note 2)
50 rnA'; 10'; 1 5 A
250 mA~ IO~ 750mA
MC7818
Min
-
rnA
rnA
-
-
-
-
-
-dB
Va
Peak Output Current (Tj::: +25°C)
Imax
13
Average Temperature Coefficient of
Output Voltage
TeVO
-
__
A
L-_~
°e
_._-"
MC7B18A. AC
ELECTRICAL CHARACTERISTICS IV,n" 27 V 10" lOA TJ" T,ow to Th,gll [Note 11 unless otherw,se noted)
Characteristics
Symbol
MC7818A
Min
Typ
-MC7818AC
MAX
Min
Typ
Unit
Max
---~--
Output Voltage (Tj = +25°C)
Va
Output Voltage
(50 mA s:. 10 'S: lOA Po ~ 15 W)
21 Vdcs Vm '( 33 Vdc
Va
1764
18
1836
1764
18
1836
173
18
187
173
18
173
70
12
40
31
45
15
25
28
10
180
180
90
Vde
Line Regulation (Note 2)
21 Vdc S V ln '; 33 Vdc, 10::: 500 mA
24 Vdc 'S: Vin ~ 30 Vdc
24VdcSV ln ,,;30Vdc,Tj=+25 DC
1-- 20 6 v~C; V,n c;~~ T,J.."_'25--"C;.~_ ~~---1---1~~~~-t--~~___1--_~7_0~-+ _ _
3_'~-~e--~-~e---~
Load Regulation (Note 2)
50 mA S 10 -:;; 1 5 A
50 mA -s;; 10"; 1 0 A
Vde
__
, 8_0 _ _ _ ...... ~
Regload
mV
35
50
12
25
55
55
22
34
55
4.5
45
0.3
0.2
004
05
05
02
50mA~10-S;;15A.Tj:;+25DC
250 mAS 10 oS 750 mA
100
100
50
-~
QUiescent Current
Tj = +25°C
'B
QUiescent Current Change
21 Vdc'; Vln:s, 33 Vdc, 10 = 500 mA
21 Vdc:S; Vln:S; 33 Vdc, TJ::: +25°C
5.0 mA:S; 10 S lOA
.lIB
Ripple Rejection
22 Vdc ~ Vln:S; 32 Vdc, f::: 120 Hz,
Tj::: +25 DC
22 Vdc:S; Vm:S; 32 Vdc, f = 120 Hz,
10" 500 rnA
RR
A Tj::: +25°C)
----
-~-
60
60
mA
mA
08
08
0.5
d8
59
59
65
65
57
Vde
V ln - Vo
2.0
2.5
2.0
Output NOise Voltage (T A::: +25 DC)
10 Hz:S; f:S; 100 kHz
Vn
10
40
10
Output ReSistance (f::. 10kHz)
AO
19
19
rnll
Short-CircUit Current Limit (TA = +25 DC)
V ln ::: 35 Vdc
'se
0.2
12
0.2
A
25
3.3
Dropout Voltage (10::: 1 0
Peak Output Current (TJ::: +25°C)
Imax
Average Temperature Coefficient of Output Voltage
TCVO
NOTES
T,ow:
o~~:; ~~~~~~X~eA
Thigh :
1.3
±2.3
2.2
A
-1 0
mV/DC
:~ ~~:g :~; ~g~~~c\e, 8
::: -40°C for MC78XXB
Load and line regulation are specified at constant Junction temperature. Changes in Vo due to heatmg effects must be taken into account
separately. Pulse testing with low duty cycle is used.
295
MC1800 Series
MC7824. B. C
ELECTRICAL CHARACTERISTICS (V in -- 33 V • IO-- 500 rnA TJ-- Tlow to Thigh [Note 11 unless a ther WI'se noted)
Characteristic
Symbol
Output Voltage (TJ::: +25°C)
Vo
Output Voltage
Vo
MC7824
Typ
Max
Min
23
24
25
23
24
25
23
24
25
-
-
-
-
-
-
22.8
24
252
Min
MC7824C
Typ
Max
Unit
Vde
22.8
24
25.2
22.S
24
25.2
-
-
-
10
50
240
-
120
-
31
14
4S0
240
-
31
14
4S0
240
-
-
40
15
240
-
-
3.6
6.0
4.6
S.O
-
60
25
4S0
-
4S0
240
-
120
60
25
4.6
SO
-
-
-
-
-
rnV
Regin
27 Vdc:::;;; Vin ~ 38 Vdc
30 Vdc ~ Vin ~ 36 Vdc
Load Regulation (TJ =+25°C, Note 2)
5.0 rnA';; 10 ,;; 1 .5 A
250 rnA';; 10 ,;; 750 rnA
MC7824B
Max
Typ
Vde
15 0 rnA,;; 10';; 1.0 A. Po ,;; 15 W)
27 Vdc::;; Vin ~ 38 Vdc
28 Vdc ~ Vin ~ 38 Vdc
Line Regulation (TJ = +25°C, Note 2)
Min
rnV
Regload
Quiescent Current (TJ:: +25°C)
IB
QUIescent Current Change
27 Vdc ~ Vin ~ 38 Vdc
28 Vdc ~ Vin ~ 38 Vdc
5.0 rnA';; 10';; 1.0 A
:>IB
Ripple Rejection
28 Vdc ~ Vm ~ 38 Vdc, f = 120 Hz
RR
Dropout Voltage (lO:: lOA, TJ::; +25°C)
Vin -
Output Resistance f = 1.0 kHz
RO
Short-Circuit Current limit (T A::: +25°C)
Ise
-
54
2.0
10
0.3
OS
0.04
0.5
56
62
-
-
20
2.5
-
10
40
-
-
20
-
0.2
Vo
Vn
mA
m.iI
-
Output NOise Voltage (T A:: +25°C)
10 Hz~ f~ 100 kHz
240
-
10
-
-
-
-
-
54
-
-
-
20
-
Vde
-
10
-
"VI
10
05
-
05
dB
~--
-
20
-
02
12
25
33
-
-
20
-
-
02
-
-
-
-
Peak Output Current (TJ;:;: +25°C)
Imax
TCVO
13
±30
-
2.2
-
-
-
~
15
22
A
- -
A
-
~,---,--
~1
-
5
rnVI
"C
-----~-~
MC7824A. AC
ELECTRICAL CHARACTERISTICS IV In ~ 33 V IO~- lOA T
~ T low to ThI h [Note
J~
~
Characteristics
Symbol
II unless otherwISe noted)
.-..
-~.
Min
MC7824A
Typ
Max
Min
MC7824AC
Typ
Max
23.5
24
245
23.5
24
245
-
Vo
Output Voltage
150 rnA';; 10';; lOA. PO';; 15 W)
273 Vdc:;;;; Vin ~ 38 Vdc
Vo
LIne Regulatron (Note 2)
27 Vdc ~ Vin:;;;; 38 Vdc, 10 = 500 rnA
30 Vdc ~ V ln ~ 36 Vdc
30 Vdc ~ V ln ~ 36 Vdc, TJ::: +25°C
267 Vdc ~ Vm ~ 38 Vdc, TJ::: +25°C
Load RegulatIon (N,ote 2)
50 mA~ IO~ 1.5 A
5.0 rnA'" 10';; 1 0 A
50mA~IO~ 1 5A, TJ;:;:+25°C
250 rnA';; 10';; 750 rnA
OUlescent Current
TJ = +25°C
23
24
25
23
24
25
-
10
15
50
10
36
60
19
36
-
240
-
31
35
14
31
40
50
-
-
-
--
RR
-
-
-
-
-
15
25
-
-
60
-
36
5.0
-
240
03
0.2
004
0.5
05
0.2
-
60
60
25
100
100
-
50
60
46
6.0
-
08
O.S
05
rnA
rnA
-
-
-dB
Vo
56
62
-
56
62
-
-
2.0
2.5
Vn
-
10
40
Output Resistance (f;:;: 1.0 kHz)
RO
-
Ise
-
20
Short-Circuit Current Limit (TA - +25°C)
Vin;:;: 35 Vdc
0.2
1.2
2.5
33
±3.0
-
Vin -
-
-
~-
Output Noise Voltage (TA;:;: +25°C)
10 Hz~ f~ 100 kHz
Dropout Voltage (10:= 1.0 A, TJ:= +25°C)
1
rnV
-
Ripple Rejection
28 Vdc ~ Vin ~ 38 Vdc, f::: 120 Hz,
TJ;:;: +25°C
28 Vdc ~ Vin ~ 38 Vdc, f::: 120 Hz,
10 = 500 rnA
-1
120
240
Regload
:>IB
Vde
rnV
-
QUIescent Current Change
27.3 Vdc:S; Vm ~ 38 Vdc, 10;:;: 500 mA
27.3 Vdc ~ Vm ~ 38 Vdc, TJ;:;: +25°C
5.0 rnA';; 10';; 1.0 A
~--,--
Vdc
Reg m
IB
---Unit
~-
Output Voltage (TJ ;:;: +25°C)
Peak Output Current (TJ:::: +25°C)
Imax
1.3
Average Temperature Coefficient of Output Voltage
TCVO
-
NOTES: 1. Tlow
rnil
~-
Vin :: 35 Vdc
Average Temperature Coeff,CIent of
Output Voltage
c-~
-
-
-
-
54
.-
2.0
-
-
10
0.2
-
-
2.2
-
A
-
-1.5
-
mV/OC
20
=-55°C for MC7SXX. A
=0° for MC7SXXC. AC
= -40°C for MC78XXB
2. Load and I!ne regulation are specified at constant junction temperature. Changes In Va due to heating effects must be taken Into account
separately. Pulse testing With low duty cycle is used.
296
Vde
"VIVO
rnll
A
MC7800 Series
TYPICAL CHARACTERISTICS
(T A = +25 0 C unless otherwise noted.)
FIGURE 1 - WORST CASE POWER DISSIPATION
versus AMBIENT TEMPERATURE (Case 221 AI
FIGURE 2 - WORST CASE POWER DISSIPATION
versus AMBIENT TEMPERATURE (Case 11
20
in
1=
<[
25
OHS _Iooc / w
16
."
~
'"
;::::
'"
12
~
~
..............
c; 80
a:
-
-50
"
""-J-
'\
0
15OC/~""
~
15
I-....
iii
c;
\.
~
I
~
25
;::
\
ROJC = 50 CIW
'"~ to ROJA = 65 0 CM
~
TJlmaxl = 1500 C
~ 50
\.
r--. "- ................ \
No Heat Smk
-25
OHS = 0
20
z
,
~
50
75
100
125
o-75
150
FIGURE 3 - INPUT OUTPUT DIFFERENTIAL AS A
FUNCTION OF JUNCTION TEMPERATURE
IMC7BXXC. AC. BI
25
10 = lOA
- -- -
10 - 200 rn~-
10 = 20 rnA--
-50
-
25
'"
«
~
t7)
-25
t---
~~
r-=:::::::: :::::::-
I- ...J
:::>«
1.5
~~
:::> w
25
50
>=
75
100
-75
125
~ 3.0
-50
-25
1.0
15
50
75
TA. AMBIENT TEMPERATURE lOCI
~
I..d::::t- --"'r--....
1
I
6.0
12
'r
..>~
'"
:::>
'"
u
:---
-....:::: ~ --...
..........:
::::::::: ~ --...
T~=~:;- -.
~
r--.
i I
r-......
TJ - 25°C
>-
:::>
>-
100 mV
10
10
=
t 0A
~ 500 mA
10 - to mA
tOO
125
in
:;; 3.0
/ ' ___
TJ = -40°C
TJ = OoC..........
~
>-
:::>
=
.
in
'"
E
t25
40
40
2.0
-
FIGURE 6 - PEAK OUTPUT CURRENT AS A
FUNCTION OF INPUT·OUTPUT DIFFERENTIAL
VOLTAGE (MC78XX. AI
FIGURE 5 - PEAK OUTPUT CURRENT AS A FUNCTION
OF INPUT·OUTPUT DIFFERENTIAL VOLTAGE
(MC78XXC. AC. BI
.
tOO
0.5
TJ. JUNCTION TEMPERATURE 1°C)
tlj
:::>
'"
u
......
>0
,
o
-25
25
50
75
TA. AMBIENT TEMPERATURE lOCI
\.
\.
--+-
~ ~ 1.0
-50
-..........
-- ---- ---
2.0
>:.
0-0
-"VO = 2% 01 Vo
- - - Extended Curve lor MC78XXB
-75
r---....
. .W out
6~
o
.......... .......
FIGURE 4 - INPUT OUTPUT DIFFERENTIAL AS A
FUNCTION OF JUNCTION TEMPERATURE
(MC78XX.AI
w
--
---- --
10 = 0 rnA
-
\.
0HS = 10 0 CM
No Heat Sink
TA. AMBIENT TEMPERATURE lOCI
10 = 500 mA
\.
.
I
o
00-
«
liHS = 5°C/W\ .
-::::..t
40
Vi
~
liHS =
'"~
,p
BJC = 5°C/W
_
liJA = 65°C/W
TJlrnaxl = 1500C-
18
24
Vin-VO. INPUT·OUTPUT VOLTAGE DIFFERENTIAL (VOLTSI
20
'f
>-
ie
>-
----..::: V
"-
--
TJ=125°C
" ~ ~/
1.0
""
,
o
o
30
TJ = 25°C
~, /
:::>
'"E
TJ = -55°C
10
20
~
~~
30
Vin-VO. INPUT·OUTPUT VOLTAGE DlFFERENTIALIVOlTSl
297
40
MC7800 Series
TYPICAL CHARACTERISTICS (continued)
(TA = 25 0 C unless otherwise noted.)
FIGURE 7 - RIPPLE REJECTION AS A FUNCTION
OF OUTPUT VOLTAGES
(MC78XXC. AC)
FIGURE 8 - RIPPLE REJECTION AS A FUNCTION
OF FREQUENCY
(MC78XXC. AC)
80
MC78XX, A
~
10 120 Hz
-o~~-
70 I-I--,-\-+-~--jr----l---+-
fo':
MC78XXC,AC
~ 60~~L-~-=~~~~~----~-4-------~~J-----+1-------~
-- --
----- ----- ---
- ~g:::~ ~~~
40
Von 0 10 V
Va o5V
10 0 20 rnA
-r-r---::-"""
V,n
10 V
11 V
14 V
19 V
---- --
----
--1----
10
MC7824C 33 V
4.0
60
8_0
14
16
18
10
12
Va, OUTPUT VOLTAGE (VOLTS)
20
22
v;ln = 11
in
::;
~ 610
..,'">-i5
-
600
---
r-.
-..
~
r--
r--
500
]
300
w
u
53
-- -.,
100
~
100
'"=>
'"=>
50
~
0
I
6
:>
=
==
-
-__
1110Hz
10 -500rnA
CL~O"F
580
- - - - 1---
30
-25
25
50
75
100
125
150
10
40
175
80
~
~
-
-
MC78XX, A
--- r---
in 60
::;
2::-
V:n = ; - : - .
Vo = 5.0 V
10 = 5 0 rnA
30
/- ~
..,
-..........
~
::; 4.0
.........
#7
0
:>
2.0
I-
~
::;
// /
l-
o
!Eo
=>
0
1.0
o
-75
-50
--25
I --
MC7~05,
A
-TJ=25°C
0
I-
~
80
v
-I-
.§.
>-
24
10
FIGURE 12 - DROPOUT CHARACTERISTICS
(MC78XX, A)
I
_I
V,n- IOV
MC78XXC, AC, B ___ f-- Vo = 5 0
10 = 20 rnA
40
16
11
Vo, OUTPUT VOL TAGE IVOl TS)
FIGURE 11 - QUIESCENT CURRENT AS A
FUNCTION OF TEMPERATURE IMC78XXC, AC, BI
60
-----'
--1
~
20
I
-50
~
-- !----t.~
TJ, JUNCTION TEMPEATURE laC)
a
--
N
I
~
lOOk
--
~
10k
I. FREQUENCY IHzl
FIGURE 10 - OUTPUT IMPEDANCE AS A
FUNCTION OF OUTPUT VOLTAGE IMC78XXC. ACI
r--Vo = 6_0 V - - r--10 = 20 rnA __
r---
620
100
10
14
FIGURE 9 - OUTPUT VOLTAGE AS A FUNCTION
OF JUNCTION TEMPERATURE (MC78XXC, AC, 81
:>
....
II
--- - - 1 - - -- tN,n10 02010rnA
- -V(RMS)
0
PART #
~
_ MC7805C
'"
MC780SC
",- 50 __ MC7808C
'"
MC7812C
Vin - 8_0 to 18 Vdc
Vo 0 5_0 V
10 0 1.0 A
""-
II
25
50
75
100
20
o
o
125
TJ, JUNCTION TEMPERATURE laC)
/~/
I I
20
40
60
80
10
INPUT VOLTAGE IVOLTS)
298
12
14
16
MC7800 Series
APPLICATIONS INFORMATION
),
Design Considerations
The MC7800 Series of fixed voltage regulators are designed
Protection that shuts down the circuit
to the power supply filter with long wire lengths, or if the output
load capacitance is large. An input bypass capacitor should be
when subjected to an e,xcessive power overload condition, Internal
selected to provide good high-frequency characteristics to insure
Short-Circuit Protection that limits the maximum current the cir-
stable operation under all load conditions, A 0,33 "F or larger
tantalum, mylar, or other capacitor having low internal impedance
at high frequencies should be chosen. The bypass capacito~should
be mounted with the shortest possible leads directly across the
regulators input terminals. Normally good constructiontechniques
should be used to minimize ground loops and lead resistancedrops
since the regulator has no external sense lead.
with Thermal
Overlo~
cuit will pass, and Output Transistor Safe-Area Compensation that
reduces the output short-circuit current as the voltage across the
pass transistor is increased.
In many low current applications, compensation capacitors are
not required. However. it is recommended that the regulator
input be bypassed with a capacitor if the regulator is connected
FIGURE 13 - CURRENT REGULATOR
Input
~
0.33 "F
r
FIGURE 14 - ADJUSTABLE OUTPUT REGULATOR
h
MC7B05
Output
'---?T----J~r.
-10
Constant
Current to
Grounded Load
K>--o-<10 k
The MC7S00 regulators can also be used as a current source
when connected as above. In order to minimize dissipation the
MC7805C is chosen in this application. Resistor R determines
the current as follows:
10 =
5V
-Fi
1 k
VOl 7.0 V to 20 V
VIN - Vo ;;>:2,0 V
+ la
IQ ~ 1.5 mA over IlOe and load changes
The addition of an operational amplifier allows adjustment to
higher or antermedlate values while retaining regulation characteristics. The minimum voltage obtainable with this arrangement if)
2.0 volts greater than the regulator voltage.
For example, a "ampere current source would require R to be a
5·ohm, 10-W resistor and the output voltage compliance would
be the IOPUt voltage less 7 volts
FIGURE 15 - CURRENT BOOST REGULATOR
FIGURE 16 - SHORT-CIRCUIT PROTECTION
MJ2955
MJ2955 or
Equ IV
'" "'1Y.
xx
:r
= 2 digits
of
or Equlv
Input
00""
I
I
I
0","",
T,
R
type number Incheattng voltage
xX
The MC7800 series can be current boosted with a PNP transistor. The MJ2955 provides current to 5.0 amperes. Resistor R
In conjunction With the VeE of the PNP de-termlnes when the
pass transistor begins concuctmg; this cirCUit is not short-Circuit
proof. Input-output differential voltage minimum is Increased by
Vee of the pass transistor.
~
- 2 digits of type number indicating voltage
The circuit of Figure 15 can be modified to provide supply protection against short CirCUits by adding a short-circuit sense resistor.
Rscland an additional PNP transistor. The current sensmg PNP
must be able to handle the short-cirCUIt current of the threeterminal regulator. Therefore. a four-ampere plastiC power tranSistor IS speCified.
299
®
MC78LOOC,AC
MOTOROLA
Series
THREE·TERMINAL POSITIVE
VOLTAGE REGULATORS
THREE·TERMINAL
POSITIVE FIXED
VOLTAGE REGULATORS
The MC78LOO Series of positive voltage regulators are inexpensive,
easy·to·use devices suitable for a multitude of applications that require a regulated supply of up to 100 mA. Like their higher powered
MC7800 and MC"78MOO Series cousins, these regulators feature
internal current limiting and th'i!"mal shutdown making them remarkably rugged. No external components are required with the
MC78LOO devices in many applications.
These devices offer a substantial perfognance advantage over the
traditional zener diode· resistor combination. Output impedance is
greatly reduced and quiescent current is substantially reduced.
P SUFFIX.
CASE 29
TO·92
,
• Wide Range of Available, Fixed Output Voltages
• Low Cost
• Internal Short·Circuit Current Limiting
• Internal Thermal Overload Protection
• No External Components Required
• Complementary Negative Regulators Offered
(MC79LOO Series)
• Available in Either ±5% (AC) or ±10% (C) Selections
Pin 1. Output
2. Ground
3, Input
0
2
o
I
0
Bottom
View
3
0
G SUFFIX
CASE 79
TO·39
REPRESENTATIVE CIRCUIT SCHEMATIC
,1ft
Input
15 k
2
Pin 1. Input
2. Output
3. Ground
(Case connected
to pin 3)
01
Output
3.8 k
STANDARD APPLlCNrION
1.2 k
02
ZI
A common ground is required between the
input and the output voltages. The input yoU-
420
age
Common
must remain typically 2.0 V above the out-
put voltage even during the low point on the
input ripple voltage.
*
= C,
is required if regulator is located an
appreciable distance from power supply
filter.
*. = Co
Device No.
'10%
MC78L05C
MC78L08C
MC78L12C
MC78L 15C
MC78L 18C
MC78L24C
Device No.
Nominal
15%
Voltage
MC78L05AC
MC78L08AC
Mt78L12AC
MC78L15AC
MC78L18AC
MC78L24AC
5.0
8.0
12
15
18
24
is not needed for stability; however,
it does improve tr_iant response.
ORDERING INFORMATION
Tempeqture R• •
Dov...
MC78LXXACG
TJoO"CIO+15O"c
Metal Can
MC78LXXACP
Tr°"Cto+l5O"c
PI_tic Tren.iltor
MC78LXXCG
T
MC78LXXCP
T J • O"c to +15O"c
0
O"c to + 150"C
Pock...
Metel Can
PI_ie Tren.istor
XX indicates nomin.1 Yoltege
MC78LOOC, AC Series
MC78LOO Series MAXIMUM RATINGS ITA
Rating
=
+125 0 C unless otherwise noted I
Value
Unit
VI
30
35
40
Vdc
Storage Junction Temperature Range
T stg
-65 to +150
Uperatm9 Junction Temperature Range
TJ
o to +150
°c
uc
Symbol
Input Voltage 12.6 V - 8.0 VI
112V-18VI
124 VI
MC78L05C, MC78L05AC ELECTRICAL CHARACTERISTICS IVI
10 V, 10 = 40 mA, CI = 0.33 pF, Co = 0.1 pF,
+125 0 C unless otherwise noted)
=
OOC
< TJ <
MC78LOSC
MC78L05AC
Symbol
Min
Typ
Max
Min
Typ
Max
Unit
Output Voltage IT J = +25 0 CI
Vo
4.6
5.0
5.4
4.8
5.0
5.2
Vdc
Input Regulation
ITJ = +25 0 C, 10 = 40 mAl
7.0 Vdc';; VI .;; 20 Vdc
8.0 Vdc ,;;VI .;; 20 Vdc
Regline
Load Regulation
Regload
Characteristic
ITJ = +250 C, 1.0 mA.;; 10';; 100 mAl
ITJ c +250 C, 1.0 rnA.;; 10';; 40 mAl
Output Voltage'
17.0 Vdc:;; VI .;; 20 Vdc, 1.0 mA.;; 10';; 40 mAl
IVI = 10V, 1.0mA';; 10';; 70 mAl
Vo
Input BIas Current
ITJ = +250 CI
ITJ = +125 0 CI
liB
Input Bias Current Change
18.0 Vdc';; VI '" 20 Vdcl
11.0mA
...=>
4.0
ci
>
2.0
10~~tmA
~
10=40~
0
o
I
1.0
r-- Jr--
./. ~
~--- r--- -- r---
10 = 1.0 mA
--
Dropout of Regulation
r-- defined as when
IS
VO=1%oIVO
.,
4.0
6.0
15
10
8.0
VI. INPUT VOLTAGE (VOL TSI
50
FIGURE 4 -
3.0
./
-
lI"
MC78L05C
VO=5.0V
10 =40mA
TJ = 25 0 C
...
100
~
115
FIGURE 5 - MAXIMUM AVERAGE POWER DISSIPATION
vanusAMBIENTTEMPERATURE-T0-92TypePa,*-
~
j----
~
;!;
""
MC78L05C
VI = 10V
Va = 5.0 V
10 =40mA
50
75
TA. AMBIENT TEMPERATURE (OCI
j---
~
iii 1.0
.........
15
4.0
<.>
...........
o
!...
;:;
....... ~
~
115
100
INPUT BIAS CURRENT versus
INPUT VOLTAGE
'f-4.0
75
TJ. JUNCTION TEMPERATURE (OCI
FIGURE 3 - INPUT BIAS CURRENT versus
AMBIENT TEMPERATURE
4.1
f
10 = 40 mA
10=100mA
!--
r--- 1--- r-- - - r--
)
o
-1
t--"...
w
'"
«
1.0
o
o
5.0
10
15
20
25
30
VI. INPUT VOLTAGE (VOLTSI
FIGURE 6 - MAXIMUM AVERAGE POWER DISSIPATION
AMBIENT TEMPERATURE - TO·39 Type Pack_
10.000
40
35
_SUI
10.000
Infinite H\t Sink
Iz
0
No Heat Sink
1000
-
i
ili
Ci
II:
w
~
1110
f
.P
r---
75
1.110
TA. AMBIENT TEMPERATURE (OCI
L
.:-..
~
3(JOClWatt Heat Sink
ROJA = 21100 CIW
PO(018.1 to 250 C • 625 mW
50
No Heat Sink
~
\
125
ISO
305
10
25
50
75
100
TA. AMBIENT TEMPERATURE (OCI
125
150
MC78LOOC, AC Series
.,
<;'- .
\
APPLICATIONS INFORMATION
Design Considerations
The MC78LOOC Series of fixed voltage regulators are designed
selected to provide good high-frequency characteristics to insure
with Thermal Overload Protection that shuts down the circuit
when subjected to an excessive power overload condition, Internal
Short-Circuit Protection that limits the maximum current the circuit will pass.
In many low current applications, compensation capacitors are
not required. However. it is recommended that the regulator
input be bypassed with a capacitor if the regulator is connected
to the power supply filter with long wire lengths, or if the output
load capacitance is large. An input bypass capacitor should be
stable operation under all load conditions. A 0.33 JJ.F or larger
tantalum, mylar, or other capacitor having low internal impl"dance
at high frequencies should be chosen. The bypass capacitor should
be mounted with the shortest possible leads directly across the
regulators input terminals. Normally good construction techniques
should be used to minimize grou'nd loops and lead resistance
drops since the regulator has no external sense lead. Bypassing the
output is also recommended.
FIGURE 7 - CURRENT REGULATOR
FIGURE 8 - ±15 V TRACKING VOLTAGE REGULATOR
+Vo
+20 V
R
-'0
Constant
Current to
Grounded Load
10 k
The MC78LOOC regulators can also be used as a current source
when connected as above. In order to minimize dissipation the
MC78L05C IS chosen in this applicatIon. Resistor R determines
the current as follows
10 k
-20 V
liB
O.331lF
= 3.8 rnA over Ime and load changes
1
-Vo
For example. a 100 mA current source would require R to be a
50-ohm, 1/2-W resistor and the output voltage compliance would
be the input voltage less 7 volts.
FIGURE 9 - POSITIVE AND NEGATIVE REGULATOR
+Vo
+V,
0.11lF
- V,
0.11lF
0.331lF
-Vo
306
®
MC78MOOC
MOTOROLA
series
•
THREE-TERMINAL
POSITIVE FIXED
VOLTAGE REGULATORS
MC78MOOC SERIES THREE-TERMINAL
POSITIVE VOLTAGE REGULATORS
The MC78MOO Series positive voltage regulators are identical to
the popular MC7800C Series devices, except that they are specified
for only one-third the output current. Like the MC7800C devices,
the MC78MOOC three-terminal regulators are intended for local, oncard voltage regulation.
Internal current limiting, thermal shutdown circuitry and safearea compensation for the internal pass transistor combine to make
these devices remarkably rugged under most operating conditions.
Maximum output current, with adequate heatsinking is 500 mAo
Pin 1. Input
20utPu'm
3. ~round
1
2~'
0
0
3
0
L
2.
Bottom
•
•
No External Components Required
Internal Thermal Overload Protection
3.
View
G SUFFIX
METAL PACKAGE
CASE 79
TO-39
(Case connected
to Pin 3)
• Internal Short-Circuit Current Limiting
• Output Transistor Safe-Area Compensation
•
Pin 1.
Packaged in the Plastic Case 221 A and Case 79
(TO-220 and Hermetic TO-39)
T SUFFIX
PLASTIC PACKAGE
CASE 221 A
(TO·220 Type)
(Heatslnk surface
connacted to Pin 2)
STANDARD APPLICATION
REPRESENTATIVE
SCHEMATIC DIAGRAM
r---~----------~~---------,-----,--~------~--olnput
100 k
A common ground 15 required between the
Input and the output voltages. The mput volt-
500
age must remam typically 2 0 V above the output voltage even dUring the low POint on the
Input ripple voltage .
.. = em IS required If regulator IS located an
appreciable distance from power supply
filter.
_. =
Co improves stability and transient response.
1-.---------l-.....----......--....--.....--o Output
ORDERING INfORMATION
DEVICE
MC78MXXCG
MC78MXXCT
I
I
I
TEMPERATURE RANGE
TJ =ooC to+l50oC
T J =OOCto+1S0oC
XX Indicates nommalvoltage
2.7 k
TYPE NO.IVOLTAGE
500
Gnd
307
MC78M05C
MC78M06C
MC78M08C
MC78M12C
MC78M15C
MC78M18C
MC78M20C
MC78M24C
5.0 Volts
6.0 Volts
8.0 Volts
12 Volts
15 Volts
18 Volts
20 Volts
24 Volts
I PACKAGE
I Metal Can
I
PlastiC Power
MC78MOOC Series
MC78MOOC Series MAXIMUM RATINGS (TA = +250 C unless otherwise noted'!
Rating
Symbol
Value
Unit
VI
35
40
Vdc
Po
6JA
Internally limited
70
°CIW
Po
6JC
I nternally Limited
5.0
°C/W
I nternally Limited
185
°C/W
Internally Limited
25
°CIW
Operating Junction Temperature Range
Po
6JA
Po
6JC
T
Operating Ambient Temperature Range
Storage Temperature Range
TA
T stg
Input Voltage (5.0 V . 18 V)
(20 V· 24 V)
Power Dissipation (Package Limitation)
Plastic Package
TA = 25°C
Derate above T A = 25°C
{,
...f''
TC = 25°C
Derate above T C = 11 OoC
Metal Package
TA = 25°C
Derate above T A = 25°C
TC = 25°C
Derate above T C = 85°C
Plastic Package
Metal Package
o to +150
o to +85
°c
-65 to +150
-65 to +150
°c
°c
°c
MC78M05C ELECTRICAL CHARACTERISTICS (VI = 10 V, 10 = 200 rnA, OoC < TJ < +125 0 C, Po < 5.0 W unless otherwise noted'!
Characteristic
Output Voltage (TJ = +250 C)
Line Regulation
Symbol
Min
Typ
Max
Vo
4.8
5.0
5.2
Unit
Vdc
mV
Regline
(TJ = +250 C)
(7.0 Vdc < VI < 25 Vdc)
(8.0 Vdc < VI < 25 Vdc)
-
3.0
1.0
100
-
20
10
100
Vo
4.75
-
5.25
Vdc
liB
-
4.5
6.0
rnA
-
0.8
0.5
40
-
/-LV
AVO/At
-
-
20
mV/l.0kHrs
RR
-
80
80
-
dB
-
VI-VO
-
2.0
-
Short-Circuit Current Limit (TJ = +250 C, VI = 35 V)
lOS
-
rnA
AVO/AT
-
300
Average Temperature Coefficient of Output Voltage
-1.0
-
mV/oC
10
-
700
-
rnA
,,
Load Regu lation
(TJ = +250 C, 5.0 rnA < 10 < 500 rnA)
(TJ = +250 C, 5.0 rnA < 10 <,200 rnA)
50
mV
Regload
Output Voltage
(7.0 Vdc < VI < 25 Vdc, 5.0 rnA < 10 < 200 rnA)
Input Bias Current (T J = +250 C)
Quiescent Current Change
(8.0 Vdc < V I < 25 Vdc)
(5.0 rnA < 10 < 200 rnA)
50
rnA
AIIB
Output Noise Voltage (T A = +250 C, 10 Hz < f < 100 kHz)
eon
Long-Term Stabil ity
Ripple Rejection (10 = 100 rnA, f = 120 Hz, 8.0 V < VI < 18 V)
(10 = 300 rnA, f = 120 Hz, 8.0 < VI < 18 V, TJ = 25°C)
Input-Output Voltage Differential
(TA = +250 C)
\
--
Vdc
(10 = 5.0 rnA)
Peak Output Current
(TJ= 25°C)
308
>
MC78MOOC Series
MC78M06C ELECTRICAL CHARACTERISTICS IVI = 11 V,IO = 200 mA, OOC < TJ < +1250 C, Po .. 5.0W unlessotherwisenoted.l
Symbol
Min
Typ
MIx
Output Voltage ITJ = +250 C)
Vo
5.75
6.0
6.25
Line Regulation
ITJ = +250 C)
18.0 Vdc .. VI .. 25 Vdc)
(9.0 Vdc .. VI .. 25 Vdc)
Regline
Load Regulation
Regload
Characteristic
ITJ
IT J
=
5.0 mA .. 10 .. 500 mAl
= +250 C, 5.0 mA .. 10 .. 200 mAl
Output Voltage
Vdc
mV
-
+250 C,
Unit
5.0
1.5
100
-
20
50
mV
-
10
120
60
Vo
5.7
-
6.3
Vdc
liB
-
4.5
6.0
mA
-
-
0.8
0.5
(8.0 Vdc .. VI .. 25 Vdc, 5.0 mA .. 10" 200 mAl
I nput Bias Current (T J
'='
+2SoC)
Quiescent Current Change
19.0 Vdc .. VI .. 25 Vdc)
15.0 mA .. 10" 200 mAl
Output NOise Voltage (T A - +2ePC, 10 Hz .. f .. 100 kHz)
Long·Term Stability
Ripple Rejection 110 - 100 mA, f - 120 Hz, 9.0 V .. VI" 19 V)
110 = 300 mA, f = 120 Hz, 9.0 V .. VI .. 19 V, T J = 25°C)
Input-Output Voltage Differential
ITA = +250 C)
·on
-
45
-
I'V
t.VOIt.t
-
-
24
mV/1.0 kHrs
RR
-
80
80
-
dB
Vdc
-1.0
-
mVloC
700
-
mA
VI'VO
Short-Circuit Current Limit IT J = +2SoC, V I ;:! 35 VI
lOS
Average Temperature Coefficient of Output Voltage
t.VOIt.T
110
mA
t.IIB
-.
2.0
270
mA
= 5.0mA)
Peak Output Current (T J = 25°C)
ITJ = 25°C)
10
-
MC78M08C ELECTRICAL CHARACTERISTICS IVI = 14 V,IO = 200mA, OOC < TJ < +1250 C, PO" 5.0W unless otherwise noted.)
Characteristic
Output Voltage IT J = +250 C)
Line Regulation
ITJ = +250 C)
110.5 Vdc .. VI .. 25 Vdc)
111 Vdc .. VI .. 25 Vdc)
Min
Typ
Max
Unit
Vo
7.7
8.0
8.3
Vdc
mV
Regline
.
Load Regulation
ITJ = +250 C, 5.0 mA .. 10" 500 mAl
ITJ " +250 C, 5.0 mA .. 10 .. 200 mAl
-
6.0
2.0
100
-
25
10
160
80
Vo
7.6
-
8.4
Vdc
liB
-
4.6
6.0
mA
-
-
0.8
0.5
50
mV
Regload
Output Voltage
110.5Vdc" VI" 25Vdc, 5.0mA" 10" 2oomA)
Input Bias Current ITJ
Symbol
= +250 C)
Quiescent Current Change
mA
t.IIB
110.5 Vdc .. VI .. 25 Vdc)
15.0 mA .. 10" 200 mAl
Output Noise Voltage IT A = +2sOC, 10 Hz .. f .. 100 kHz)
eon
Long-Term Stability
t.VOIt.t
Ripple Rejection 110 = 100 mA, f = 120 Hz, 11.5 V .. VI" 21.5 V)
110 = 300mA, f = 120 HZ,l1.5 V .. VI" 21.5 V, TJ = 25°C)
.RR
Input-Output Voltage Differential
ITA = +250 C)
VI'VO
-
-
-
52
-
I'V
-
32
mVI1.0 kHrs
BO
BO
dB
-
2.0
-
Vdc
Short-Circuit Current Limit ITJ = +250 C, VI = 35 V)
lOS
-
250
mA
t.VOIt.T
-
-
Average Temperature Coefficient of Output Voltage
1I0=5.0mA)
-1.0
-
mV/oC
10
-
700
-
mA
Peak Output Current
ITJ = 25°C)
309
MC78MOOC Series
MC78M12C ELECTRICAL CHARACTERISTICS IVI = 19 V, 10 = 200 mA, oOe /oo
- -- -
C;w __ ._
<"~
H~
~fi<4>:-
()
____
~~ i~
..!!.!!.!:~/NK
...!!!!J.NITE NEA
I)
1-
-~c-T
.......
0
;:
0.5
~
04
03
E
02
0.1
""
i,\\
"''\
l-
HJC> 50 CIW
r- POIMAX, > 7 5 W
"j
50
25
\.
\
100
75
TA. AMBIENT TEMPERATURE (OC,
05
~
_
0.4
03
rP
02 _ HJC > 25 0 C/W
o125
150
1'l
r
........
-
::::---.
""" ~=OOI
...........
I
....... .........
0.50
0.25
~
TJ=25 0C--""';::
~
3.0
6.0
9.0
12
15
1B
21
70
§
60
24
~
50
~
40
w
II:
"""~
a;
",,-
........
o
75
100
TA. AMBIENT TEMPERATURE (OC,
150
125
80
'"z
e
TJ>
o
50
\.
~
~
~
moc............
~
::>
§
.........
I
90
b r--.. ~
1.00
I-
e
"j'
\.
'\ \\
100
~
:IE
I-
'\.
............
FIGURE 4 - RIPPLE REJECTION AS A FUNCTION
OF FREQUENCY
1.26
::;
~ 0.76
K
...........
FIGURE 3 - PEAK OUTPUT CURRENT AS A FUNCTION OF
INPUT-OUTPUT DIFFERENTIAL VOLTAGE
~
AT I
PO(MAX, > 7.6 W
\.
I
.........
............
OHS>2~
C
ffi
~NK
~>'ooCIW ...........
"'J}1o
""
t--,.
27
...........
30
V, = 10V
Vo = 5.0 V
10 = 20 mA
20
10
I
o
30
10
V,·VO.,NPUT-OUTPUT VOLTAGE DIFFERENTIAL (VOLTS,
100
f. FREQUENCY (Hzl
313
1.0 k
10 k
MC78MOOC Series
APPLICATIONS INFORMATION
Design Consid..ations
to the power supply filter with long wire lengths, or if the output
load capacitance is large. An input bypass capacitor should be
The MC78MOOC Series of fixed voltage regulators are designed
with Thermal Overload Protection that shuts down the circuit
when subjected to an excessive po\Ner overload condition, J nternal
Short-Circuit Protection that limits the maxi.mum current the circuit will pass, and Output Transistor Safe-Area Compensation that
reduces the output short-circuit current as the voltage across the
selected to provide good high·frequency characteristics to insure
stable operation under all load conditions. A 0.33 /olF or larger
tantalum, mylar, or other capacitor having low internal impedance
at high frequencies should be chosen. The bypass capacitor should
be mounted with the shortest possible leads directly across the reg·
ulators input terminals. Normally good construction techniques
should be used to minimize ground loops and lead resistance drops
since the regulator has no external sense lead.
pass transistor is increased.
In many low current applications, compensation capacitors are
not required. However, it is recommended that the regulator
input be bypassed with a capacitor if the regulator is connected
FIGURE 5 - CURRENT REGULATOR
FIGURE 6 - ADJUSTABLE OUTPUT REGULATOR
Output
Input
R
~
Constant
Current to
Grounded Load
0.1
"F
10 k
The MC7800C regulators can also be used as a current source
when connected as above. In order to minimize dissipation the
MC7805C is chosen in this application. Resistor R determines
the current as follows:
5V
10=
R
Va, 7 OV t020 V
+ IQ
V,N -- Vo ~20V
IQ'" 1.5 mA over line and load changes
The addition of an operational amplifier allows adjustment to
higher or intermediate values while retaining regulation character·
istics. The minimum voltage obtainable With this arrangement I')
2.0 volts greater than the regulator voltage.
For example, a 500 mA current source would require R to be a
10·ohm, 10·W resistor and the output voltage compliance would
be the input voltage less 7 volts.
FIGURE 8 - SHORT-CIRCUIT PROTECTION
FIGURE 7 - CURRENT BOOST REGULATOR
MJ2955
MJ2955
or EQuiv
or Equlv
Input
Input
k.....,......... Output
R
1.0/J.FI
xx
==
2 digits of tYpe number Indicating voltage.
x X == 2 dIgits of type number Indicatlllg voltage.
The MC78MOOC series can be current boosted with a PNP transis·
tor. The MJ2955 provides current to 5.0 amperes. Resistor R
In conjunction With the Vee of the PNP determines when the
pass transistor begins conauctmg; this cirCUit IS not short-circuit
proof. Input·output differential voltage minimum IS Increased by
Vse of the pass tranSistor.
The circuit of Figure 7 can be modified to provide supply protec·
tion against short circuits by adding a short-circuit sense resistor,
RSC/and an additional PNP transistor. The current sensing PNP
must be able to handle the short-circuit current of the three·
terminal regulator. Therefore, a two"8mpere plastic power tran·
slstor IS speCified.
314
®
MC78TOO
MOTOROLA
Product
Series
Previe~
THREE-TERMINAL
POSITIVE FIXED
VOLTAGE REGULATORS
3-TERMINAL POSITIVE VOLTAGE REGULATORS
These voltage regulators are monolithic integrated circuits designed
as fixed-voltage regulators for a wide variety of applications including
local, on-card regulation. These regulators employ internal current
limiting, thermal shutdown, and safe-area compensation. With
adequate heatsinking they can deliver output currents in excess of 3.0
amperes. Although designed primarily as a fixed voltage regulator,
these devices can be used with external components to obtain
adjustable voltages and currents.
•
•
•
•
•
•
Output Current in Excess of 3.0 Amperes
No External Components Required
Internal Thermal Overload Protection
Internal Short-Circuit Current Umiting
Output Transistor Safe-Area Compensation
Output Voltage Offered in 2% and 4% Tolerance"
KSUFFIX
METAL PACKAGE
CASE 1
(TO·3TYPE)
PIN I.
INPUT
OUTPUT
GROUND
2.
CASE
SCHEMATIC DIAGRAM
TSUFFIX
PLASTIC PACKAGE
CASE 221A
'rO·220 TYPE
PIN 1.
INPUT
GROUND
OUTPUT
2.
3.
1
2
3
STANDARD APPLICATION
Input
a
MC78TXX
' Output
Co"
Cin*
O.33J1F
.
A common ground is required between the
input and the output voltages. The input voltage
must remain typically 2.0 V above the output
voltage even during the low point on the input
ripple voltage.
XX = these two digits of the type number indicate
voltage .
• = Cin is required if regulator is located an
appreciable distance from power supply
ORDERING INFORMATION
Device
Output Voltage
Tolerance
MC78TXXK
MC78TXXAK
4%
2%*
MC78TXXCK
MC78TXXACK
4%
2%*
MC78TXXCT
MC78TXXACT
4%
2%*
filter.
Temperature Range
Package
•• = Co
is not needed for stability; however, it
does improve transient response.
- 55 to + 150°C
o to
XX Indicates nommal voltage
Metal Power
+ 125°C
TYPE NO./VOLTAGE
Plastic Power
xx Indicates nominal voltage
*2% regulators are available In 5, 12 and 15 volt deVIces
This document contains Information on a product under development Motorola reserves the
right to change or discontinue thiS product Without notice
315
MC78T05
MC78T06
MC78T08
MC78T12
5.0 Volts
6.0 Volts
S.OVolts
12 Volts
M<;78T15
MC78TI8
MC78T24
15 Volts
18 Volts
24 Volts
®
MC7900C
MOTOROLA
Series
\ MC7900C SERIES THREE-TERMINAL
NEGATIVE VOLTAGE REGULATORS
THREE-TERMINAL
NEGATIVE FIXED
VOLTAGE REGULATORS
The MC7900C Series of fixed output negative voltage regulators
are intended as complements to the popular MC7800C Series devices.
These negative regulators are available in the same seven-voltage
options as the MC7800C devices. In addition, two extra voltage
options commonly employed in MECL systems are also available
in the negative MC7900C Series.
Available in fixed output voltage options from -2.0 to -24 volts,
these regulators employ current limiting, thermal shutdown, and
safe-area compensation, - making them remarkably rugged under
most operating conditions. With adequate heat-sinking they can
deliver output currents in excess of 1.0 ampere.
•
No Exfernal Components Required
•
I nternal Thermal Overload Protection
•
rnternal Short-Circuit Current Limiting
•
Output Transistor Safe-Area Compensation
•
Packaged in the Plastic Case 221 A and Case 1
(TO-220 and Hermetic TO-3)
K SUFFIX
METAL PACKAGE
'CASE 1
ITO-3 TYPE)
(bottom view)
T SUFFIX
PLASTIC: PACKAGE
CASE 221 A
Pin 1. Ground
2. Input
SCHEMATIC DIAGRAM
3. Output
(Heatsink surface
connected to Pin2)
STANDARD APPLICATION
A common ground is required between the
,..----+--t--oVo
input and the output voltages. The input voltage must remain typically 2.0 V more negative
even during the'f\igh point on the input ripple
voltage.
XX
::=
these two digits of the type number indi-
cate voltage.
*
03
=
Cin is required if regulator is located an
appreciable distance from power supply
filter.
** == Co improves stability and transient response.
ORDERING INFORMATION
DEVICE
DEVICE TYPE/NOMINAL OUTPUT VOL TAG
MC7902C - 2.0 Volts
MC7905C - 5.0 Volts
MC7905.2C - 5.2 Volts
MC7906C - 6.0 Volts
MC790ac - 8.0 Volts
MC7912C -12 Volts
MC7915C - 15 Volts
MC7918C - 18 Volts
MC7924C - 24 Volts
316
ITEMPERATURE RANGE I PACKAGE
MC79XXCK 1
T J = 0° C to +150° C
1 Metal Power
MC?9XXCTI
T J OOOOCto+150 o C
I Plastic Power
XX indicates nominal voltage
MC7900C Series
MC7900C Series MAXIMUM RATINGS (TA = +25 0 C unless otherwise noted.1
Symbol
Rating
Input Voltage (2.0 V - 18 VI
(24 VI
Value
Unit
-35
-40
VI
Vdc
Power Dissipation
Plastic Package
T A = +25 0 C
Derate above T A == +250 C
Po
Internally Limited
Watts
l/ROJA
15.4
mW/oC
TC = +25 0 C
Derate above T C :;; +950 C (See Figure 1)
Po
l/ReJC
I nternally limited
200
mW/oC
Watts
Metal Package
Po
Internally Limited
+250 C
l/ReJA
22.2
Watts
mW/oC
TC = +250 C
Derate above T C = +650 C
Po
l/ROJC
I nternal1v Limited
182
mW/oC
T stg
-6510+150
°c
TJ
Oto+150
°c
T A = +25 0 C
Derate above T A
=
Storage Temperature Range
Junction Temperature Range
Watts
THERMAL CHARACTERISTICS
Characteristic
.'
Thermal Reslstaf1ce, Junction to Ambient - Plastic Package
Symbol
Max
Unit
ROJA
65
45
°C/W
ROJC
5.0
5.5
°c/w
- Metal Package
Thermal Resistance, Junction to Case
- Plastic Package
- Metal Package
MC7902C ELECTRICAL CHARACTERISTICS ( VI = -10 V, 10 = 500 rnA, OOC VO/t>t
-
-
20
JJ.V
mV/l0k Hrs
RR
-
65
-
dB
I VI-Vol
-
3.5
-
Vdc
6VO/6T
-
-1.0
-
mV/oC
10 = 1.0 A, TJ = +25 0 C
Average Temperature Coefficient of Output Voltage
10 = 5.0 rnA, OOC ':;;TA ':;;+125 0 C
317
MC7900C Series
MC7905C ELECTRICAL CHARACTERISTICS IVI = -10 V, 10 = 500 rnA, ooc
u
... 1.0
~
3.0
6.0
9.0
12
'" '"
~ 60
50
0
~
,
100
75
125
TA. AMBIENT TEMPERATURE (DC)
150
Vin=-tt V
Va = -6.0 V
10 = 20 rnA
15
18
'r--,.
1""
~
'" 40
...
"
21
t-
...Ul
~
iii:
.......
",-
'"
24
27
0
o
30
100
10
lOOk
10 k
1.0 k
f. FREQUENCY (Hz)
FIGUR E 6 - OUTPUT VOLTAGE AS A FUNCTION
OF JUNCTION TEMPERATURE
80
...Ul
'"
...'"
'\
~
I-- t-'
z
FIGURE 5 - RIPPLE R EJECTION AS A FUNCTION OF
OUTPUT VOLTAGES
i=
1"'-
'\
IVI-VOI.INPUT·OUTPUT VOLTAGE DIFFERENTIAL (VOLTS)
z
."
r- ~ f"'.
BD
:5!
~
o
o
~
.......
iii
0.5
iii 70
:5!
.............
100
~
5o
9
i"--,
FIGURE 4 - RIPPLE REJECTION AS A FUNCTION
OF FREQUENCY
2. 5
;;;
~
--
;-.....
Po (Max) = 15 W
TA. AMBIENT TEMPERATURE (oC)
...'"
I"'"'--.
.........
0.5
0.4
0.3
9JC - 5.5° CIW
0.2 8JA = 45 0 CIW
rP
I"
100
13
a:
'\
\
75
>
9HS = 50
5.0 t"'"---4.0
9HS = 15 0 CIW
3.0
2i
1,\
I"
9JC = 50 CIW
o. 2 9JA = 65 0 CIW
Po (M,x) = 15W
O. I 25
50
~
"-
....
~ ~;3
§_
;;;
"- .\
r--......
~N: HEATSINK
10
.......
........
crw-- r-
0
INFINITE HEAT SINK
or--+--l
i ~:
FIGURE 2 - WORST CASE POWER DISSIPATION AS A
FUNCTION OF AMBIENT TEMPERATURE (TO-3)
6.26
-\
60
g 6.22
f = 120 Hz
10 = 20 rnA
AVin = 1.0 V(RMS)
f----
~...
r-......
§!
... 6.14
-
............. r-
~
iii:
",- 50
'" 6.18
~
~
o
~ 6.10
'"
40
2.0
4.0
6.0
8.0
10
12
14
16
18
20
6.06
-25
22
Va. OUTPUT VOLTAGE (VOLTS)
322
/'
-_.
/'"
/'
./
..---
--
-- ..
~
i
Vin=-tt V
va = -6.0 V
10 = 20 rnA
1
.1
I
+25
+50
+75
+100
+125
TJ.JUNCTION TEMPERATURE (OC)
+150
+175
MC7900C Series
TYPICAL CHARACTERISTICS Icontinuedl
FIGURE 7 - QUIESCENT CURRENT AS A FUNCTION
OF TEMPERATURE
DEFINITIONS
Line Regulation - The change in output voltage for a change in
the input voltage. The measurement is made under conditions of
low dissipation or by using pulse techniques such that the average
chip temperature is not significantly affected.
5. 2
or--..
!'-..
Load Regulation -- The change in output voltage for a change in
t-.....
8
load current at constant chip temperature.
..........
f"--..
6
VO' -6.0 V -
........
10' 20 mA
"4.2
o
25
50
Maximum Power Dissipation -, The maximum total device dissipation for whiCh the regulator will operate within specifications.
Vin=-11 V
75
TJ. JUNCTION TEMPERATURE lOCI
...........
100
Input Bias Current - That part of the Input current that is not
delivered to the load.
-
Output NOise Voltage· The rms ae voltage at the output, with
constant load and no Input ripple, measured over a specified frequency range.
125
Long Term Stability
Output voltage stability under accelerated
life test conditions with the maximum rated voltage listed in the
devices' electrical characteristics and maximum power dissipation.
323
MC7900C Series
APPLICATIONS INFORMATION
Design Considerations
to the power supply filter with long wire lengths, or If the output
load capacitance is large. An Input bypass capacitor should be
selected to prOVide good high-frequency characteristics to insure
stable operation under all load conditions. A 0.33 ,uF or larger
tantalum, mylar, or other capacitor having low Internal Impedance
at high frequencies should be chosen. The bypass capacitor should
be mounted with the shortest possible leads directly across the regulators input terminals. Normally good construction techniques
should be used to minimi~e ground loops and lead resistance
drops since the regulator has no external sense lead. Bypassing the
The MC7900C Series of fixed voltage regulators are designed
with Thermal Overload Protection that shuts down the Circuit
when subjected to an excessive power overload condition, Internal
Short-Circuit Protection that limits the maximum current the cir-
CUit will pass, and Output Transistor Safe-Area Compensation that
reduces the output short-circuit current as the volta:ge across the
pass transistor IS Increased.
,'~"
In many low current applications, compensation capacitors are
not required
However, It IS recommended that the regulator
Input be bypassed with a capacitor If the regulator IS connected
output is also recommended.
FIGURE 8 - CURRENT REGULATOR
FIGURE 9 - CURRENT BOOST REGULATOR
(-5.0 V@ 4.0 A, with 5.0 A current limiting)
~10
V
0.56
I nput "-~~V\I'~--'--.(
-5.0 V
) , - - - - - - -.....- . Output
10 = 200 mA
1--o-.--YVv----+-....
Input
VO~10V
T+ 1 .0 ,uF
-r+ 1 .0 ,uF
-+-+----------<+>-----•• Gnd
Gnd ••
The MC7902, -2.0 V regulator can be used as a constant current
source when connected as above. The output current is the sum of
resistor R current and quiescent bias current as follows:
Gnd..--------~---
When a boost transistor IS used, short-circuit currents are equal
to the sum of the series pass and regulator limits, which are
measured at 3.2 A and 1.8 A respectively in this case. Series pass
limiting is approximately equal to 0.6 VJRSC' Operation beyond
this point to the peak current capability of the MC7905C is possible if the regulator is mounted on a heat sink; otherwise thermal
shutdown will occur when the additional load current is picked up
by the regulator.
2V
10 ~R+ IB
The qUiescent current for this regulator is typically 4.3 mAo
The 2.0 volt regulator was chosen to mmimize dissipation and to
allow the output voltage to operate to within 6.0 V below the
Input voltage.
FIGURE 10 - OPERATldNAL AMPLIFIER SUPPLY
1±15 V@ LOA)
+20 V
Input
0.33,uF
Gnd
__---*_~Gnd
* Mounted on comma n heat sink, Motorola MS-1 0 or equivalent.
FIGURE 11 - TYPICAL MECL SYSTEM POWER SUPPLY
1-5.2 V @ 4.0 A and -2.0 V @ 2.0 A; for PC Board)
-12 V
+15 V
Output
Input
-5.2 V
.... Output
lr--VV\r----~-
1N4001
or Equiv
Gnd
-2.0 V
),-~j\f'~----'--+---
'"~
10° :.~mA
4.0
>
f-
W
1004~~
~I 2.0
he ~
~
!;
~
100100mA
-2.0
0
t-
-8.0
>
-0.5
10 01.0 mA
I--
Dropout 01 Regulation is
defined as when
VO"'2%oIVO
o
o
-10
25
VI. INPUT VOLTAGE (VOLTS)
FIGURE 4 -
4.2
4.0
~
I'-.....
r-........
-.........
z
w
6
:,.
-4.0
l!
fr-
f-
"
)
o
b:"
e ;5'" -1.0
I
o
-2.0
;:;;
<5 2:. -1.5
f-
>. ~
f-
~
g
10 ° 70mA
;::
Vo ° -5.0 V
TJ ° 25 0 C
60
i!
-2.5
MC7~L05C
;:;;
100
~
L
~
D.
300 CJWatl Heat Sink
0
ROJA ° 200·CIW
PO(ma,) 10 250C ° 625 mW
50
No HeafSmk
\
75
100
125
150
TA, AMBIENT TEMPERATURE (OCI
'330
,I 0
25
.1.
50
75
100
TA, AMBIENT TEMPERATURE (OC)
125
150
®
SG 1525AjSG 1527A
SG2525AjSG2527A
SG3525AjSG3527A
MOTOROLA
PULSE WIDTH MODULATOR CONTROL CIRCUIT
The SG1525A/1527A series of pulse width modulator controlcircuits offer improved performance and lower external parts count
when Implemented for controlling all types of switching power
supplies. The device includes a +5.1 volt ±1 % reference and an
error amplifier with a common-mode range including the reference
voltage to eliminate external divider resistors. A sync input to the
oscillator enables multiple Units to be slaved together, or a single
unit can be synchrOnized to an external system clock AWlde range
of dead time IS programmable with a single resistor between the
CT pin and the Discharge pin. Other features included are soft-start
circUitry reqUiring only an external timing capacitor. Ash utdown pin
controls both the soft-start clrcuitryand the output stages, allowing
fast output turn-off with soft-start recycle turn-on. Undervoltage
lockout keeps the outputs off when VCC is less than the reqUired
level for normal operation The output stages are a totem-pole
design capable of sinking and sourcing In excess of 200 mA. The
SG1525A series output stage features NOR Logic, giving a low
output for an off state The SG1527A utilizes OR LogiC which results
In a high output level when off. These deVices are available in
MllltarY,lndustrial and Commercial temperature ranges and feature'
•
80 to 35 Volt Operation
•
51 Volt ±1% Trimmed Reference
•
100 Hz to 400 kHz OSCillator Range
•
Separate OSCillator Sync Pin
•
Adjustable Dead Time
•
Input Undervoltage Lockout
•
Latching PWM to Prevent Multiple Pulses
•
Dual Source/Sink Output Current. ±400 mA Peak
PULSE WIDTH MODULATOR
CONTROL CIRCUITS
SILICON MONOLITHIC
INTEGRATED CIRCUITS
-
N SUFFIX
PLASTIC PACKAGE
CASE 648
1
J SUFFIX
CERA,MIC PACKAGE
CASE 620
PIN CONNECTIONS
INV Input
Vref
N I Input
VCC
Sync
OSC Output
FUNCTIONAL BLOCK DIAGRAM
Discharge
9 Compensation
Soft-Start
(Top View)
ORDERING INFORMATION
Device
331
Temperature Range
Package
SG1525AJ
SG1527AJ
-55 to +125°C
-55 to +125°C
Ceramic Dip
SG2525AJ
SG2525AN
SG2527AJ
SG2527AN
-40 to +85°C
-40 to +85°C
-40 to +85°C
-40 to +85°C
Ceramic DIp
Plastic DIp
Ceramic DIp
Plastic Dip
SG3525AJ
SG3525AN
SG3527AJ
SG3527AN
Oto+70oC
Ceramic DIp
Plastic Dip
Ceramic Dip
Plastic DIp
o to +70°C
o to +70o e
Oto+70oe
Ceramic DIp
SG1525A, SG1527A, SG2525A, SG2527A, SG3525A, SG3527A
MAXIMUM RATINGS (Note 1)
Rating
Symbol
Value
Unit
VCC
+40
Vdc
Collector Supply Voltage
Vc
+40
Vdc
Logic Inputs
-0.3 to +5.5
V
Analog Inputs
-
-0.3 to VCC
V
Output Current, Source or Sink
10
±500
mA
Reference Output Current
Iref
50
mA
Oscillator Charging Current
-
5.0
Power Dissipation (Plastic & Ceramic Package)
Note 2, TA = +25°C
Note 3, TC= +25°C
Po
Supply Voltage
mA
mW
1000
2000
Thermal Resistance Junction to Air
Plastic and C~ramic Package
ReJA
100
°C/W
Thermal Resistance Junction to Case
Plastic and Ceramic Package
ReJC
60
°C/W
Operating Junction Temperature
Storage Temperature Range
Ceramic Package
TJ
+150
°C
Tstg
-65 to +150
-55 to +125
°C
TSolder
+300
°C
Plastic Package
Lead Temperature (Soldering, 10 Seconds)
NOTES
Values beyond which damage may occur
Derate at 10 mW/oC for ambient temperatures above +50oC
Derate at 16 mW/oC for case temperatures above +25°C
RECOMMENDED OPERATING CONDITIONS
Characteristic
Symbol
Min.
Max.
Unit
VCC
+8.0
+35
Vdc
Collector Supply Voltage
Vc
+4.5
+35
Vdc
Output Sink/Source Current
(Steady State)
(Peak)
10
0
0
±100
±400
Supply Voltage
mA
Reference Load Current
Iret
0
20
mA
OSCillator Frequency Ra nge
fosc
0.1
400
kHz
OSCillator Timing Resistor
RT
2.0
150
kfl
OSCillator Timing Capacitor
CT
0.001
0.1
/-IF
Deadtlme Resistor Range
RO
0
500
Operating Ambient Temperature Range
SG1525A. SG1527A
SG2525A, SG2527A
SG3525A, SG3527A
TA
-55
-40
0
332
fl
°C
+125
+85
+70
SG1525A, SG1527A, SG2525A, SG2527A, SG3525A, SG3527A
ELECTRICAL CHARACTERISTICS (VCC
0
+20 Vdc, TA
0
Tlow to Thigh [Note 4J, unless otherwise specified)
SG1525A/2525A
SG.1527 A12527 A
Characteristic
SG3525A
SG3527A
Symbol
Min
Typ
Max
Min
Typ
Max
Unit
Vref
5.05
5.00
REFERENCE SECTION
Reference Output Voltage (TJ
5.10
5.15
5.10
5.20
Vdc
Line Regulation (+8.0 V';; VCC';; +35 V)
Regline
-
10
20
-
10
20
mV
Load Reg ulation (0 mA';; IL';; 20 mAl
Regload
-
20
50
-
20
50
mV
-,Vref/ -,T
-
20
50
-
20
50
mV
-
525
Vdc
0
+25°C)
Temperature Stability
Total Output Vanatlon
Includes Line and Load Regulation
5.00
-,Vref
-
5.20
495
over Temperature
ISC
-
80
100
-
80
100
mA
VN
-
40
200
-
40
200
,uV rms
S
-
20
50
-
20
50
mV/khr
-
±2.0
±60
-
:,:20
±60
%
-
±O 3
±10
-
±10
±20
%
...l.fosc
-
±30
±60
-
±30
±60
%
Minimum Frequency (RT = 150 kll, CT=OI MF)
f m1n
-
100
_.
-
MaXimum Frequency (RT = 20 kfl, CT
f max
400
-
22
Short ClfCUlt Current
(Vref 0 0 V, TJ 0 +25°C)
Output NOise Voltage
(10Hz';; f';; 10kHz, TJ
Long Term Stability ITJ
0
0
+25°C)
+125°C) (Note 5)
OSCILLATOR SECTION (Note 6, unless otherwise specified)
-
Initial Ace uracy (T J = +25°C)
Frequency Stability with Voltage
...l.fosc
1+8.0 V';; VCC';; +35 V)
-,VCC
Frequency Stability with Temperature
----:rr-
~.
1.0 nF)
0
400
-
-
100
Hz
kHz
~,
Current Mirror (lRT
= 2 a mA)
c------------
--
Clock Width (T J = +25°C)
-,
Sync Threshold
~-
17
17
20
3.0
35
-
30
35
--
03
05
1.0
03
05
10
-
1 2
20
2.8
1 2
20
28
Sync Input Current (Sync Voltage = +3 5 V)
V
-
--
10
2.5
-
10
25
mA
0
20
~--
22
~-
--
mA
-~
-
.-
c----~
----,
,~---.
ERROR AMPLIFIER SECTION (VCM
-
-
. - --,
C--'
Clock Amplitude
~~--
V
~---
MS
.-e----
~-'--'
+5.1 V)
,--------
.-~.-
-~
Input Offset Voltage
Via
-
05
50
-
2.0
10
mV
Input Bias Current
lIB
-
10
10
-
10
10
MA
110
-
-
10
-
-
10
MA
~--~---
..- - - .
Input Offset Current
DC Open Loop Gain (RL? 10 Mll)
AVOL
60
75
-
60
75
-
dB
Gam Bandwidth Product
IAVOl 0 dB, TJ +25°C)
GBW
10
20
-
10
2.0
-
MHz
O
0
Low Level Output Voltage
0.2
0.5
V
02
05
VOH
3.8
5.6
-
38
56
-
Common Mode Rejection RatiO
(+1 5 V,;; VCM';; +5.2 V)
CMRR
60
75
-
60
75
-
Power Supply Rejection RatiO
(+8.0 V,;; VCC';; +35 V)
PSRR
50
60
-
50
60
-
dB
VOL
-
-
~'
High Level Output Voltage
V
-dB
PWM COMPARATOR SECTION
Minimum Duty Cycle
DCmin
-
-
0
-
-
0
%
MaXimum Duty Cycle
DC max
45
49
-
45
49
-
%
Input Threshold, Zero Duty Cycle (Note 6)
VTH
0.6
0.9
-
0.6
0.9
-
V
Input Threshold, Maximum Duty Cycle (Note 6)
VTH
-
3.3
3.6
-
3.3
36
V
liB
-
0.05
1.0
-
0.05
10
MA
Input Bias Current
333
SG1525A, SG1527A, SG2525A, SG2527A, SG3525A, SG3527A
ELECTRICAL CHARACTERISTICS (Continued)
SG1525A/2525A
SG1527A/2527A
I
I
Max
Min
50
80
25
0.4
0.6
-
0.4
1.0
-
-
0.2
1.0
0.4
2.0
-
18
17
19
18
-
6.0
7.0
-
-
Svmbol
Min
Soft-Start Current (Vsh utdown
-
25
Soft-Start Voltage (Vshutdown
-
-
-
-
Characteristic
SG3525A
SG3527A
TVp
I
I
Max
Unit
50
80
,..A
0.4
0.6
V
0.4
1.0
rnA
0.2
1.0
0.4
2.0
18
17
19
18
-
8.0
6.0
7.0
8.0
V
200
-
-
200
,..A
ns
TVp
SOFT-START SECTION
= 0 V)
= 2.0 V)
Shutdown Input Current (Vshutdown = 2.5 V)
OUTPUT DRIVERS (Each Output. Vc = +20 V)
Output Low Level
(lslnk
(Isink
V
VOL
= 20 rnA)
= 100 rnA)
Output High level
(lsource = 20 rnA)
(lsource = 100 rnA)
= High)
=+35 V (Note 7)
Rise Time (Cl = 1.0 nF. TJ = 25°C)
Fall Time (Cl = 1.0 nF. TJ = 25°C)
Under Voltage lockout (V8 and V9
Collector leakage. Vc
Shutdown Delay
(VSD = +3.0 V. Cs
-
V
VOH
VUl
1C(leak)
= 0, TJ =+25°C)
=+35 V
Supply Current, VCC
tr
-
100
600
-
100
600
tf
-
50
300
-
50
300
ns
tds
-
0.2
0.5
-
0.2
0.5
,..s
ICC
-
14
20
-
14
20
rnA
NOTES.
4 Tlow= -55°C for SG1525A/1527A
-40°C for SG2525A12527A
O°C for SG3525A/3527A
Thigh::: +125°Cfor SG1525A/1527A
+85°C for SG2525A/2527A
+70°C for SG3525A/3527A
5 Since long term stability cannot be measured on each device before shipment. this specification IS an englneenng estimate of average stability
from lot to lot
Tested at fose::: 40 kHz (RT::: 3 6 kfl, CT= 001 j..tF. RD = O!!)
7 Applies to SG 1525A/2525A/3525A only, due to polarrty of output pulses
APPLICATION INFORMATION
Shutdown
Op~ions
(see block diagram. front page)
3. Applying a positive-going signal to the Shutdown pin
(10) will provide the most rapid shutdown of the outputs if a soft-start capacitor is not used at Pin 8. An
external soft-start capacitor at Pin 8 will slow shutdown response due to the discharge time of the softstart capacitor. Dishcarge current is approximately
twice the charging current.
1. An external open collector comparator or transistor
can be used to pull down the Compensation pin (9).
This will set the PWM latch and turn off both outputs.
Pulse-by-pulse protection can be accomplished if the
shutdown signal is momentary. since the PWM latch
will be reset with each clock pulse.
2. Shutdown can also be accomplished by pulling down
on the SOFT-START pin (8). When using this approach.
shutdown will not affect the amplifier compensation
network; however. if a SOFT-START capacitor is used.
it must be discharged, possible slowing shutdown
response.
4. The Shutdown terminal can be used to set the PWM
latch on a pulse-by-pulse basis if there is no external
capacitance on Pin 8. Soft-start characteristics may
still be accomplished by applying an external capacitor. blocking diode and charging resistor to the Compensation pin (9),
334
SG1525A, SG1527A, SG2525A, SG2527A, SG3525A, SG3527A
TYPICAL CHARACTERISTICS
FIGURE 1 - SG1525A OSCILLATOR SCHEMATIC
FIGURE 2 -
OSCILLATOR CHARGE TIME versus RT
20 0
10 0
..
L
L
ffi " ",
0
... ...
,-y
"" ~"",""~~
"" ",,"" ~j'"
'~L
~J.... ".c.....
" "'.....
",""
0
".......
r..,.......
(,,),
V
V
0
*RO = 0 n
ij1==
R'
D ')=
-
0
1
1/
/
2.
1/
oV
2.0
5.0 10
L
20
Rl TCl
1mmu -
50 100 200 50010002000 500010.000
CHARGE liME II'S)
osc Output
FIGURE 3 - OSCILLATOR OISCHARGE TIME versus RO
FIGURE 4 - SG1525A ERROR AMPLIFIER SCHEMATIC
-.
lL
5001'-'-.-rTrrrr---,--,-/..--r-"--'TTTT-',-'--'IITTrTTTr - l
II
4001~~~H+H-~+-+frt~#-~+-~t+~~~
~~ 30011--+-I4-f++l+~~"-LJ~'.--,...
...~ '{if- ~'{ . . If~t::: ,:;c::' $' ~~Jt- ~~
t::>.....::;"
"': .
~
t-
d- i'~r-iJ
fo~/ +-"') "'::. I--~ 20011--+-~+H~~1I~-F-t-~H+[~/+-t-r1-1~H+H-~
c
lJ
V V
~
~100
IJ
'"
o
0.2
0.5
1/
V
[.IV
1.0
2.0
II
V
V~
V
5 0 10
20
DISCHARGE TIME II'S)
UI
ill
50 100
200
FIGURE 6 - SG1525A OUTPUT CIRCUIT
(1/2 CIRCUIT SHOWN)
FIGURE 5 - ERROR AMPLIFIER OPEN-LOOP
FREQUENCY RESPONSE
10011----~----1-----I----4----+----+----+---~
~ 8011===1=:;;;c:=j:;::::::-i--i----T----t----t---i
~
0
~
40,-
Z
~
..........
~"O'
" 1'0 ...z+----+----t-----t----i
h •
i::
~
~-1',,"f'~-__P....__+--;;::-__±c;-_+-____i
~ I '~~~X==lH~RZ:----2(...0-k-+__-J
+
I~;
~Z.'---po-,,+----1
....
-20l,;--_:l,--7b--,J;;-;:---..\-;:---;-;;inr-' -\";;"i1;-"
"'m.---~
1.0
10
100
1.0k 10k
lOOk
1.0M 10M
f. FREOUENCY (Hz)
5Dk
Clock
335
10k
F/F
10k
PWM
SG1525A, SG1527A, SG2525A, SG2527A, SG3525A, SG3527A
FIGURE 7 - SG1525A/2525A/3525A
OUTPUT SATURATION CHARACTERISTICS
C;; 4. Or--
t:;
0
~
Vee =+20 V
rIA =25°C
3. 5
~
« 3. 0
<.0
t:;
0
;,-
~
2. 5
~~
;z
0
2. 0
;:::
~ I. 5
:::>
I--"
~
>-
..
~ I. 0
";>=
~
o. 5
0
0.01
~urt. Sat. (Ve-V OH)
Sink at. VoLi
-I---'
0.2 O.J
0.5 07
0.02 0.03 0.0 .0 0.1
10. OUTPUT SOURCE OR SINK CURRENT (AMPS)
FIGURE 8 - SINGLE ENDED SUPPLY
1
FIGURE 9 - PUSH-PULL CONFIGURATION
+Vsupply
For smgle·ended supplies. the dnver outputs are grounded.
The
Vc
terminal
IS
In conventional push-pull bipolar deSigns, forward base
drive IS controlled by Rl-R3. Rapid turn-off times for the
power devices are achieved with speed-up capacitors C1
and C2.
sWitched to ground by the totem-pole
source transistors on alternate oscillator cycles.
FIGURE 10 - DRIVING POWER FETS
FIGURE 11 - DRIVING TRANSFORMERS IN A
HALF-BRIDGE CONFIGURATION
Cl
C2
The low source impedance of the output drivers provides
rapid charging of power FET input capacitance while minimizing external components.
Low power tra nsformers ca n be drive n directly by the SG 1 525A.
Automatic reset occurs during deadtime, when both ends of the
primary winding are switched to ground.
336
SG1525A, SG1527A, SG2525A, SG2527A, SG3525A, SG3527A
FIGURE 12 - LAB TEST FIXTURE
337
5G1526
SG2526
5G3526
@ MOTOROI.A
PULSE WIDTH MODULATION CONTROL CIRCUIT
The SG1526 is a high performance pulse width modulator integrated circuit intended forfixed frequency switching regulators and
other power control applications.
Functions included in this IC are a temperature compensated
voltage reference, sawtooth oscillator, error amplifier, pulse width
modulator, pulse metering and steering logic, and two high current
totem pole outputs ideally suited fordriving the capacitance of power
FETs at high speeds.
Additional protective features incl ude soft-start and undervoltage
lockout. digital current limiting, double pulse inhibit, adjustable dead
time and a data latch for single pulse metering. All digital control
ports are TIL and B-series CMOS compatible. Active low logic design
allows easy wired-OR connections for maximum flexibility. The
versatility of this device enables! implementation in single-ended
or push-pull switching regulators that are transformerless ortransformer coupled. The SG1526 is specified Iover the full military junction temperature range of -55°C to +150 oC. The SG2526 is specified
over a junction temperature range of -40°C to +150°C while the
SG3526 is specified over a range of OOC to +125°C.
• 8.0 to 35 Volt Operation
PULSE WIDTH MODULATION
CONTROL CIRCUITS
SILICON MONOLITHIC
INTEGRATED CIRCUITS
I
-
-
N SUFFIX
PLASTIC PACKAGE
CASE 707
18 1
J SUFFIX
CERAMIC PACKAGE
CASE 726
• 5.0 Volt ±1 % Trimmed Reference
•
1.0 Hz to 400 kHz Oscillator Range
•
Dual Source/Sink Current Outputs: ±100 mA
•
Digital Current Limiting
PIN CONNECTIONS
• Programmable Dead Time
• Undervoltage Lockout
•
Single Pulse Metering
• Programmable Soft-Start
• Wide Current Limit Common Mode Range
• Guaranteed 6 Unit Synchronization
BLOCK DIAGRAM
Vref
Ground
Sync 12
Rdeadtime 11
RT
Top View
ReS8t
Csoft-start
Compensation
ORDERING INFORMATION
+Error
Device
SG1526J
+c.s
SG2526J
SG2526N
-C.S.
SG3526J
SG3526N
338
Junction Temper
sture Range
-55 to +150oC
-40 to +150 oC
o to +125°C
Package
Ceramic DIP
Ceramic DIP
Plastic DIP
Ceramic DIP
Plastic DIP
SG1526, SG2526, SG3526
MAXIMUM RATINGS (Note 1)
Rating
Symbol
Value
Unit
VCC
+40
Vdc
Collector Supply Voltage
Vc
+40
Vdc
Logic Inputs
-0.3 to +5.5
V
Analog Inputs
-
-0.3 toVCC
V
Output Current, Source or Sink
10
±200
mA
Reference Output Current
Iref
50
mA
Logic Sink Current
-
15
Power Dissipation (Plastic & Ceramic Package)
Note 2, T A = +25°C
Note 3, T C = +25°C
PD
Supply Voltage
mA
mW
1000
3000
Thermal Resistance Junction to Air
(Plastic and Ceramic Package)
ROJA
100
°C/W
Thermal Resistance Junction to Case
(Plastic and Ceramic Package)
ROJC
42
°C/W
Operating Junction Temperature
TJ
+150
°C
Tstg
-65 to +150
°C
TSolder
:t300
°C
Storage Temperature Range
Lead Temperature (Soldering, 10 Seconds)
Notes:
1 Values beyond which damage may occur
2. Derate at 10 mW/oC for ambient temperatures above +50 cC
3 Derate at 24 mW/oC for case temperatures above +25°C
RECOMMENDED OPERATING CONDITIONS
Characteristic
Supply Voltage
Collector Supply Voltage
Symbol
Min
Max
VCC
+8.0
+35
Vdc
Vc
+4.5
+35
Vdc
mA
Unit
Output Sink/Source Current (Each Output)
10
0
±100
Reference Load Current
Iref
0
20
rnA
Oscillator Frequency Range
fosc
0.001
400
kHz
Oscillator Timing Resistor
RT
2.0
150
k!1
Oscillator Timing Capacitor
CT
0.001
20
I'F
3.0
50
Available Deadtime Range (40 kHz)
Operating Junction Temperature Range
SG1526
SG2526
SG3526
TJ
-55
-40
0
339
%
°C
+150
+150
+125
SG1526, SG2526, SG3526
ELECTRICAL CHARACTERISTICS (VCC = +15 Vdc. TJ = T,ow to Thigh [Note 41 unless otherwise specified)
Characteristic
REFERENCE SECTION (Note 5)
Reference Output Voltage (TJ = +25°C)
Line Regulation
(+8.0 V';;; VCC';;; +35 V)
Vref
4.95
5.00
5.05
4.90
5.00
5.10
V
Regline
-
10
20
-
10
30
mV
Reg'oad
-
10
30
50
mV
-
15
50
-
10
aVref/aTJ
15
50
mV
IINref
4.90
5.00
5.10
4.85
5.00
5.15
V
ISC
25
50
100
25
50
100
mA
Reset Output Voltage
(Vref = +3.8 V)
-
-
0.2
0.4
-
0.2
0.4
V
Reset Output Voltage
(Vref = +4.8 V)
-
2.4
4.8
-
2.4
4.8
-
V
±3.0
±8.0
%
0.5
1.0
%
Load Regulation. 0 mA';;;IL';;; 20 mA
Temperature Stability
Total Reference Output Voltage Variation
(+8.0 V.;;; VCC';;; +35 V. 0 mA';;;IL';;; 20 mAl
Short Circuit Current
(Vref=OV)
UNDERVOLTAGELOCKOUT
OSCILLATOR SECTION (Note 6)
-
±3.0
±8.0
-
0.5
1.0
-
-
7.0
10
-
3.0
5.0
%
fmin
-
-
1.0
-
-
1.0
Hz
f max
400
-
-
400
-
-
kHz
Sawtooth Peak Voltage
(VCC= +35 V)
Vosc(P)
-
3.0
3.5
-
3.0
3.5
V
Sawtooth Valley Voltage
(VCC = +8.0 V)
Vosc(V)
0.5
1.0
-
0.5
1.0
-
V
Input Offset Voltage
(RS';;; 2.0 kn)
V,O
-
2.0
5.0
-
2.0
10
mV
Input 8ias Current
liB
-
-350
-1000
-2000
nA
',0
-
35
100
-
-350
Input Offset Current
DC Open Loop Gain
(RL;;'10 MO)
AVol
64
72
-
High Output Voltage
(VPin 1-VPin 2;;' +150 mV. Isource = 100 /lA)
VOH
3.6
4.2
Low Output Voltage
(VPin 2-VPin 1 ;;. +150 mV. Isink = 100 /lA)
VOL
-
Common Mode Rejection Ratio
(RS';;; 2.0kn)
CMRR
Power Supply Rejection Ratio
(+12 V';;; VCC';;; +18 V)
Initial Accuracy (TJ = +25°C)
-
Frequency Stability over Power Supply Range
(+8.0 V';;; VCC';;; +35 V)
~
Frequency Stability over Temperature
(aTJ = T,ow to Thigh)
~
Minimum Frequency
(RT = 150 k O. CT= 20 /IF)
Maximum Frequency
(RT = 2.0 kO. CT = 0.001 /IF)
aVCC
aTJ
ERROR AMPLIFIER SECTION (Note 7)
35
200
nA
60
72
-
dB
-
3.6
4.2
-
V
0.2
0.4
-
0.2
0.4
V
70
94
-
70
94
-
dB
PSRR
66
80
-
66
80
-
dB
Minimum Duty Cycle
(Vcompensation = +0.4 V)
DCmin
-
-
0
-
-
0
%
Maximum Duty Cycle
(Vcompensation = +3.6 V)
DC max
45
49
-
45
49
-
%
,..
PWM COMPARATOR SECTION (Note 6)
340
SG1526, SG2526, SG3526
ELECTRICAL CHARACTERISTICS (Continued)
Characteristic
DIGITAL PORTS (SYNC. SHUTDOWN. RESET)
Output Voltage - High logic level
(Isource ~ 40 I'A)
VOH
2A
4.0
-
2A
4.0
-
V
Output Voltage - low logic level
lisink ~ 3.6 mAl
VOL
-
0.2
OA
-
0.2
OA
V
Input Current - High LogiC Level
(VIH ~ +2.4 V)
IIH
-
~125
-200
-
-125
-200
I'A
Input Current - Low Logic Level
(Vll ~ +0.4 V)
III
-
~225
-360
-
~225
~360
I'A
90
100
110
80
100
120
mV
liB
-
-3.0
~10
-
-3.0
-10
I'A
-
-
0.1
OA
-
0.1
04
V
50
100
150
50
100
150
I'A
12.5
12
13.5
13
-
12.5
12
13.5
13
-
0.2
12
0.3
2.0
-
0.2
1.2
0.3
2.0
CURRENT LIMIT COMPARATOR SECTION (Note 8)
Sense Voltage
Vsense
(RS~50!l.)
Input Bias Current
SOFT-START SECTION
Error Clamp Voltage
(Reset
~
+OA V)
CSolI-Start Chargmg Current
(Reset ~ +2A V)
ICS
OUTPUT DRIVERS
(Each Output, Vc ~ +15 Vdc unless otherwise specified)
Output High level
Isource:: 20 mA
Isource ~ 100 mA
VOH
Output Low Level
Isink ~ 20 mA
Isink ~ 100 mA
VOL
Collector leakage, Vc
Rise Time (Cl
Fall Time (Cl
~
~
V
V
~
+40 V
1000 pF)
1000 pF)
Supply Current
(Shutdown ~ +OA V, VCC
RT ~ 4.12 k!l.)
~
Iqleakl
-
50
150
-
50
150
tr
-
0.3
0.6
-
0.3
0.6
tf
-
0.1
0.2
-
0.1
0.2
I's
ICC
-
18
30
-
18
30
mA
+35 V,
Notes
4 Tlow::: -55°C for SG 1526
-40°C for pG2526
O°C for SG3526
Thigh::;: +150 oC for SG1526/2526
+125°C for SG3526
5. IL:: 0 mA unless otherwise noted.
6. fosc::: 40 kHz (RT::: 4.12 kfl ±1 %,
CT ~ 0.Q1 ~F ±1 %, RD ~ 0 nl
7. OV~VCM~+5.2V
8. OV~ VCM ~ +12 V
341
I'A
fI's
SG1526, SG2526, SG3526
TYPICAL CHARACTERISTICS
FIGURE 2 - REFERENCE VOLTAGE AS A
FUNCTION SUPPLY VOLTAGE
FIGURE 1 - SG1526 REFERENCE STABILITY
OVER TEMPERATURE
5 ~V
Spee
L
o
r-- : - -
iot l-- ~
---
"-r-'
2::
--
5.0 - - -
~
'"§; 4.0
-
~
~
.. ,
II
r-/
1.0
V
/
/
-75
-50
-25
25 ,50
75
100
TJ, JUNCTION TEMPERATURE (DC)
125
1.0
150
2.0
3.0 4.05.0
10
20
VCC, SUPPLY VOLTAGE (V)
30 40
FIGURE 4 - CURRENT LIMIT
COMPARATOR THRESHOLD
FIGURE 3 - ERROR AMPLIFIER OPEN LOOP
FREQUENCY RESPONSE
8o.----,---,----,----,----~---r----,---,
70~--~--~----4_--_+----+_---+----~--~
2:: 60 ~--~--_1----4_--_+----+_--_+----t_--~
_ 80
~
~5.0r---~--~----~--_t----+---_+----~--~
~ 60
i:i
'"
>4.0~--~--_1----~--_+----+_--_+----t_--~
'" 40
~
<=>
~
PF~
>. 20
~
«
2
-
100
130 f----f--+---\-I-+--+---f----+---I
1
~2.0~--~--_1----~~~----+_--_+----~--~
CComp
1.0
f---+--+--+t---t--f---+--+--j
1IIIIIIIIIIIIIIIi IIIIII
10
100
1.0K
10K
lOOK
f, FREOUENCY (Hz)
1.0 M
25
10 M
8.0
2::
7.0
'"
;'0
6.0
'"~
200
./
,/
25
3
20~_+-1r~_+~~--~-+--+-+~4_~H_--+_~
'"<=>>=
§
1.5~_+-1--1-+~~--~-+--+-+~4_~~--+_~
>
4.0
~
3.0
'"
<=>
>
I~
175
FIGURE 6 - OUTPUT DRIVER SATURATION
VOLTAGE AS A FUNCTION OF SINK CURRENT
FIGURE 5 - UNDERVOLTAGE LOCKOUT
CHARACTERISTIC
2:: 5.0
50
75
100
125
150
OIFFERENTIALINPUT VOLTAGE (mV)
... ---
~ l.ot-_+----I-+~.++--~_+--+-+~+~~--+_~
CJ
>-=>
2.0
1.0
V
b
1.0
~ 05~-_+--t_1-+~44--_+_+--~_+_+4.~H_--+_~
25'"
,-- - +---1 +'++t+---f--l-~f---+""""'TITmrnn~mrn-~mrn
2.5
~
..'"
2.0
w
0:
~
~ 1. 5
z
i
:::>
--
1.0
~
u
:>
O. 5
"
....
0
"
to
i:i
0:
'"z
I-
::E 10
~.,.
>=
5.0ffi1lj
2.0 ~N~",;W!_~N~",-!!'"!~N*"""":J",~O!-'-;!o~o~o~o~";lo~o;-',!o"""o~o:;-'-'
0
2.0
5.0
10
20
..-
20
Vc SINK CURRENT (mAl
50
100
200
0000
6 6
FIGURE 9 - SG1526 ERROR AMPLIFIER
0c::id
0 0
c::i""':N
Lri..-N
LnOO
og
OSCILLATOR PERIOD (m'l
FIGURE 10 - SG1526 UNDERVOLTAGE LOCKOUT
Vee
To Reset
To Driver A
To Driver B
- Error
+ Error
FIGURE 11 - SG1526 PULSE PROCESSING LOGIC
Memory
F/F
sYnc~
0
SQ
PWM
D
R
o
Clock
PWM
Metering
F/F
The metering FLIP-FLOP IS an asynchronous
data latch which suppresses high frequency
oscillations by allowing only one PWM pulse
per oscillator cycle.
The memory FLIP-FLOP prevents double pulsing In a push-pull configuration by remembering which output produced the last pulse.
343
SG1526, SG2526, SG3526
APPLICATIONS INFORMATION
FIGURE 12 - EXTENDING REFERENCE
OUTPUT CURRENT CAPABILITY
FIGURE 13 -
ERROR AMPLIFIER CONNECTIONS
Negative
r--J"M-tI. . Output
Voltage
c*~
__
_ ..J
+
27
Vcc-....-'VVv-C~
Vref
Positive
Gnd
L----J\I\/Ir-l_ Output
G nd
Voltage
Gnd-------------------t--------~~-
*May be reqUired
with some types
of tra nSJstors
Vout
FIGURE 14 -
11
OSCILLATOR CONNECTIONS
SG1526
12
FIGURE 15 -
=
Vref
(:~)
FOlDBACK CURRENT LIMITING
Sync
RD
Gnd
Imax =
FIGURE 16 -
( 0.1 V + Vout R1 )
R1 + R2
RS
FIGURE 17 -
SG1526 SOFT-START CIRCUITRY
+12 V
_I----....--------{)
ISC=
OlV)
(FlS
DRIVING VMOS POWER FETS
0---.------------,
/I
The totem-pole output drivers of the SG 1526
are ideally suited for drivmg the input capacitance of power FETs at high speeds.
344
SG1526, SG2526, SG3526
FIGURE 19 - FLY8ACK CONVERTER
WITH CURRENT LIMITING
FIGURE 18 - HALF-8RIDGE
CONFIGURATION
+Vcr~t-------------~t-------~
Supply
C1
C2
In the above circuit, current limiting is accomplished by using the current limit comparator
output to reset the soft-start capacitor.
FIGURE 20 - SINGLE-ENDED CONFIGURATION
+V Supply o-~I---____
FIGURE 21 - PUSH-PULL CONFIGURATION
r---_.. To
+V Supply 0---11-----------,
Output
Filter
345
®
TL431
series
MOTOROLA
Specifications and Applications Information
PROGRAMMABLE
PRECISION REfERENCES
PROGRAMMABLE PRECISION REFERENCES
SILICON MONOLITHIC
INTEGRATED CIRCUITS
The TL431 integrated circUits are three-terminal programmable
shunt regulator diodes. These. monolithic IC voltage references
operate as a low temperature coefficient zener which is programmable from Vrefto 36 volts with two external resistors. These devices
exhibit a wide operating current range of 1.0to 100 mAwlth a typical
dynamic impedance of 0.22 D. The characteristics of these references make them excellent replacements for zener diodes in many
applications such as digital voltmeters, power supplies, and op amp
circUitry. The 2.5 volt reference makes it convenient to obtain a stable
reference from 5.0 volt logic supplies, a nd since the TL431 operates
as a shunt regulator, it can be used as either a positive or negative
voltage reference.
Pm 1 Reference
2 Anode
3 Cathode
•
Programmable Output Voltage to 36 Volts
•
Low Dynamic Output Impedance, 0 22 D Typical
•
Sink Current Capability of 1 0 to 100 mAo
•
Equivalent Full-Range Temperature CoeffiCient of 50 ppm;oC
TYPical
•
Temperature Compensated for Operation over Full Rated Operating Temperature Range
•
Low Output NOise Voltage
Cathode
Reference
(R)
~
(K)
Anode
(A)
SYMBOL
LP SUFFIX
PLASTIC PACKAGE
·CASE 29
TO-92
2
3
(Top View)
Referencei------------, Cathode
+
(R)
:
iI
(K)
P SUFFIX
PLASTIC DUAL-IN-LiNE PACKAGE
CASE 626
I
I
I
I
IL __________ ..JI
Anode (A)
FUNCTIONAL BLOCK DIAGRAM
Cathode (K)
(Top View)
CathodeOa
NC
2
Reference
7 NC
NC
3
6
NC 4
Anode
5 NC
JG SUFFIX
CERAMIC DUAL-IN-LiNE PACKAGE
CASE 693
Reference
(R)
ORDERING INFORMATION
Device
INTERNAL SCHEMATIC
Component values are nominal
Anode (A)
346
Temperature
Range
Package
TL431 CLP
o to +70°C
Plastic TO-92
TL431 CP
o to +70 o C
o to +70°C
Plastic DIP
TL431CJG
TL4311LP
-40 to +85°C
Plastic TO-92
Ceramic DIP
TL4311P
-40 to +85°C
Plastic DIP
TL4311JG
-40 to +85°C
Ceramic DIP
TL431 MJG
-55 to +125°C Ceramic DIP
TL431 series
MAXIMUM RATINGS (Full operating ambient temperature range applies unless
otherwise noted.)
Rating
Symbol
Value
VKA
37
V
IK
-100 to +150
mA
Cathode To Anode Voltage
Cathode Current Range, Continuous
Unit
Reference Input Current Range, Continuous
Iref
-0.05 to +10
mA
Operating Junction Temperature
TJ
150
°c
Operating Ambient Temperature Range
TL431 M
TL431 I
TL431 C
TA
Storage Temperature
°C
-55 to +125
-40 to +85
to +70
o
Ran~e
-65 to +150
Tstg
Total Power Dissipation @ TA = 25°C
Derate above 25°C Ambient Temperature
LP SuffiX Plastic Package
P Suffix Plastic Package
JG SuffiX Ceramic Package
PD
Total Power D,ss,patiOn @TC= 25°C
Derate above 25°C Case Temperature
LP Suffix Plastic Package
P Suffix Plastic Package
JG SuffiX Ceramic Package
PD
°c
W
0.775
110
1.25
W
1.5
3.0
3.3
THERMAL CHARACTERISTICS
Symbol
LP Suffix
Package
P Suffix
Package
JG Suffix
Package
Unit
Thermal Resistance,
Junction to Ambient
ROJA
178
114
100
°C/W
Thermal Resistance,
Junction to Case
ROJC
83
41
38
°C/W
Symbol
Min
Max
Unit
VKA
Vref
36
V
IK
1.0
100
mA
Characteristics
RECOMMENDED OPERATING CONDITIONS
Condition/Value
Cathode To Anode Voltage
Cathode Current
ELECTRICAL CHARACTERISTICS (Ambient temperature at 25°C unless otherWise noted)
Characteristic
Symbol
Reference Input Voltage (Figure 1)
VKA = Vref, IK = 10 mA
Vref
Reference Input Voltage Deviation Over
Temperature Range. (Figure 1, Note 1)
VKA = Vref, IK = 10 mA
LlVref
Ratio of Change in Reference Input Voltage
LlVref
to Change In Cathode to Anode Voltage
LlVKA
IK = 10 mA (Figure 2), LlVKA = 10 V to Vref
LI VKA = 36 V to 10 V
Min
TL431 M
Typ
Max
2.440 2.495 2550
-
15
44
Min
TL431 I
Typ
Max
2.440 2.495 2.550
-
7.0
30
Min
TL431C
Typ
Max
2.440 2.495 2.550
-
30
17
Unit
V
mV
mV/V
-
-1.4
-1.0
-2.7
-2.0
-
-1.4
-1.0
-2.7
-2.0
-
-1.4
-1.0
-2.7
-2.0
Reference Input Current (Figure 2)
IK = 10 rnA, R1 = 10 k, R2 = 00
Iref
-
1.8
4.0
-
1.8
4.0
-
1.8
4.0
jJ.A
Reference Input Current Deviation Over
Temperature Range. (Figure 2)
IK= 10mA, R1 = 10k, R2=00
Lllref
-
1.0
3.0
-
0.8
2.5
-
0.4
1.2
jJ.A
Minimum Cathode Current For Regulation
VKA = Vref (Figure 1)
Imin
-
0.5
1.0
-
0.5
1.0
-
05
1.0
mA
Off-State Cathode Current (Figure 3)
VKA = 36 V, Vref = 0 V
loff
-
2.6
1000
-
2.6
1000
-
2.6
1000
nA
Dynamic Impedance (Figure 1, Note 2)
VKA = Vref, LlIK = 1.0 mA to 100 mA
f";; 1.0 kHz
IZkal
-
0.22
0.5
-
0.22
0.5
-
0.22
0.5
n
347
TL431 series
FIGURE 1 -
TEST CIRCUIT FOR VKA = Vref
FIGURE 2 -
TEST CIRCUIT FOR VKA > Vref
FIGURE 3 - TEST CIRCUIT FOR loff
Input Q--'WIr-.....----QVKA
Input
o--""",.--<~--o
VKA
,Ioff
Rl
R2
Note 1
The deviation parameter D. Vref IS defined as the differences between the maximum and minimum values obtained over the full operating
ambient temperature range that applies.
-- -.:;-,..----
Vrel Max
I::. Vrel = Vrel Max - Vrel Min
Vrel Min
Tl
T2
AMBIENT TEMPERATURE
The average temperature coefficient of the reference mput voltage, a Vref. is defined as:
ppm
a Vref
°e
aVref can be positive or negative depending on whether Vref
Min orVref Max occurs atthe lower ambient temperature. (Referta
Figure 6)
Example: I::. Vrel = 8.0 mV and slope is positive, Vrel @ 25°e =
2.495 V, I::. TA = 70 0 e
0.008 x 10 6
oNrel = 70 (2.495) = 45.8 ppm/De
Note 2
The dynamic impedance Zka is defined as:
When the device is programmed with two external resistors, R1 anq R2. (refer to Figure 2) the total dynamic impedance of the circuit is
defined as:
348
Tl431 series
FIGURE 4 - CATHODE CURRENT versus
CATHODE VOLTAGE
FIGURE 5 - CATHODE CURRENT versus
CATHODE VOLTAGE
150
BOO
VKA ° Vre!
TA ° 25°C
VKA ° Vre!
TA ° 25°C
_ 600
'"'"'[~r'
'"'"'f~r"
«
3
.IK
z
~ 400
/
g 200
/'
L-1.0
./"
I0
-200
-I 0
30
20
1.0
VKA. CATHODE VOLTAGE (VI
FIGURE 6 2600
'> 2580
'""'W'"
~
254o
'">->
252 0 V -
Vre!
!
I
I
-
>~ 242 0
240 0
-55
-25
25
IKolOmA
I
10 k
Vre! Min ° 2440 mV -
I
I ----125
o
-25
-55
FIGURE 8 - CHANGE IN REFERENCE INPUT
VOLTAGE versus CATHODE VOLTAGE
0
I~
IK
1
100
>~
11K
B
R2 Vre!
~
~
-
10
20
30
40
VKA. CATHODE VOLTAGE (VI
00 1
-55
-25
25
50
TA. AMBIENT TEMPERATURE (OCI
349
75
100
125
TL431 series
FIGURE 10 - DYNAMIC IMPEDANCE
versus FREQUENCY
FIGURE 11 - DYNAMIC IMPEDANCE
versus AMBIENT TEMPERATURE
0.32oc---.------,---,---,----~-_r--,
10 0
TA 25°C
L'>IK 1.0 rnA to 100 rnA
1.0 k
_
tt]:"'.'
'-'
'"
~
50
+
VKA 0 Vrel
L'>IK = lOrnA to 100 rnA
I"; 1.0 kHz
,.,'-'V'~r--:-:r---QOut put
'"-
O. I
0.240f-----+'-__- + - - - - j - - - - f - - - 7 " \ ' - - - + - - - - I
o
0
;'f
'"
10K
1.0 K
lOOK
10M
0200~55--~-2~5--~OC--~2~5--~5~O--~7-5--~-~125
10 M
I. FREQUENCY (MHz)
TA, AMBIENT TEMPERATURE 1°C)
FIGURE 12 - OPEN LOOP VOLTAGE GAIN
versus FREQUENCY
FIGURE 13 -
0
0
IK
;
50
A~
.,~~
'" 40
~
30
g 20
!
'"oz
I~
10 k
1.0 k
100 k
VKA = Vrel
IK = 10 rnA
TA = 25°C
0
,
0
-10
Gnd
I
'\
-'
o
~
0"-1-
.,),
'\
10
't.
-
'\
0..
g;
230
+
B.25
k
""
ili
25°C
0
tlK
['-
o
lOrnA TA
0
Output
:;;:
'"
Vref
=2.0V
TL431 series
FIGURE 29 - SIMPLE 400 mW PHONO AMPLIFIER
FIGURE 28 - LINEAR OHMMETER
3BV
25V
TI = 330 n to B.O n
5.0 k
1%
50
k
1%
500
k
1%
330
10K
1.0kn
-VVout
*Thermalloy
THM 6024
Rx
-=
Rx = Vout •
A
V
Package
Range
FIGURE 30 - HIGH EFFICIENCY STEP-DOWN
SWITCHING CONVERTER
150I'h@2.0A
V m = 10t020V
Q--1_-+----i.:
'n......_ _......~
4.7 k
47k
CONDITIONS
RESULTS
Lme Regulation
TEST
Vin = 10 V to 20 V, 10 = 1.0 A
53 mV
(11%1
Load Reg ulation
Vin = 15 V, 10 = OA to 1.0 A
25 mV
(0.5%1
Output Ripple
Vin = 10 V, 10 = 1.0 A
50 mV p _p PAR.D.
Output Ripple
Vin = 20 V, 10 = 1.0 A
Efficiency
Vin = 15 V,
10 = 1.0 A
353
100 mV p _p PAR.D.
B2%
V out = 5.0 V
lout = 1.0 A
@ MOTOROLA
TL494
TL495
Specifications a'nd Applications
Information
SWITCHMODE
PULSE WIDTH MODULATION
CONTROL CIRCUITS
SWITCHMODE
PULSE WIDTH MODULATION
CONTROL CIRCUITS
SILICON MONOLITHIC
INTEGRATED CIRCUITS
The TL494 and TL495 are fixed frequency, pulse width modulation control circuits designed primarily for Switch mode power
supply control. These devices feature:
Tl494
• Complete Pulse Width Modulation Control Circuitry
• On-Chip Error Amplifiers
• On-Chip 5 Volt Reference
• Adjustable Dead-Time Control
• Uncommitted Output Transistors For 200 mA Source Or Sink
• Output Control For Push-PUll Or Single-Ended Operation
• On-Chip 39 Volt Zener (TL495 Onlyl
III
16
~ ~
16
1
-
N SUFFIX
PLASTIC PACKAGE
CASE 648
-I
I!!
J SUFFIX
CERAMIC PACKAGE
CASE 620
• Output Steering Control (TL495 Onlyl
Tl495
PIN CONNECTIONS
TL494
i
_
• On-Chip Oscillator With Master Or Slave Operation
TL495
N SUFFIX
PLASTIC PACKAGE
CASE 707
J SUFFIX
CERAMIC PACKAGE
CASE 726
ORDERING INFORMATION
Device
TL494CN
TL494CJ
The TL494C/495C are specified over the commercial operating
range of DoC to 70°C. The TL4941/4951 are specified over the industrial range of - 25°C to 85°C. The TL494M is specified over the
full military range of -55°C to 125°C.
354
Temperature
Range
o To 70°C
o To 70'C
Package
Plastic DIP
Ceramic DIP
TL4941N
-25 To 85'C
Plastic DIP
TL4941J
-25 To 85'C
Ceramic DIP
TL494MJ
-55To 125°C
TL495CN
TL495CJ
o To 70'C
o To 70°C
Ceramic DIP
Plastic DIP
Ceramic DIP
TL4951N
-25 To 85'C
Plastic DIP
TL4951J
-25 To 85'C
Ceramic DIP
TL494, TL495
FIGURE 1 -
BLOCK DIAGRAM
Steering Control
Output Control
VCC
13(14)
(B)
D
FlipFlop
Dead-Time
Ck
0 r---+---L~
4(4)
Dead-Time
Control
12(12)
~O.7
mA
14(14)
Ref. Out.
RZ
3(3)
Feedback/P.W.M.
Comparator Input
Error Amp
1
16(18)
Error Amp
2
FIGURE 2 - TIMING DIAGRAM
Capacitor CT
Feedback/P.W.M. Comp.
Dead-Time Control
Flip-Flop
Clock Input
Flip-Flop
o
Flip-Flop
Q
Output Q2
Emitter
Output
Control
355
(15)
7(7)
Vz
GND
#
1#)
~
TL494
~ TL495
TL494, TL495
Description
The TL494/495 are fixed-frequency pulse width modulation control circuit, incorporating the primary building blocks required for the control of a sWitching power
supply. (See Figure 1.) An internal-linear sawtooth oscillator is frequency-programmable by two external
components, RT and CT' The oscillator frequency is
determined by:
fosc ~
voltage at the feedback pin varies from 0.5 to 3.5 V. 80th
error amplifiers have a common-mode input range from
- 0.3 V to (VCC - 2 V), and may be used to sense powersupply output voltage and current. The error-amplifier
outputs are active high and are ORed together at the
non-inverting input of the pulse-width modulator comparator. With this configuration, the amplifier that demands minimum output on time, dominates control of
the loop.
When capacitor CT is discharged, a positive pulse is
generated on the output of the dead-time comparator,
which clocks the pulse-steering flip-flop and inhibits the
output transistors, 01 and 02. With the output-control
connected to the reference line, the pulse-steering flipflop directs the modulated pulses to each of the two
output transistors alternately for push-pull operation.
The output frequency is equal to half that of the oscillator. Output drive can also be taken from 01 or 02,
when single-ended operation with a maximum on-time
of less than 50% is required. This is desirable when the
output transformer has a ringback winding with a catch
diode used for snubbing. When higher output-drive currents are required for single-ended operation, 01 and
02 may be connected in parallel, and the output-mode
pin must be tied to ground to disable the flip-flop. The
output frequency will now be equal to that of the
oscillator.
The TL494!495 has an internal 5 V reference capable
of sourcing up to 10 mA of load current for external bias
circuits. The reference has an internal accuracy of + 5%
with a thermal drift of less than 50 mV over an operating
temperature range of 0 to 70°C.
The TL495 contains an on-chip 39 volt zener diode for
high voltage applications where Vec is greater than 40
volts, and an output steering control that overrides the
internal control of the pulse-steering flip-flop. (Refer to
the functional table shown in figure 3.)
1.1
RT • CT
Output pulse width modulation is accomplished by
comparison of the positive sawtooth waveform across
capacitor CT to either of two control signals. The NOR
gates, which drive output transistors 01 and 02, are
enabled only when the flip-flop clock-input line is in its
low state. This happens only during that portion of time
when the sawtooth voltage is greater than the control
signals. Therefore, an increase in control-signal amplitude causes a corresponding linear decrease of output
pulse width. (Refer to the timing diagram shown in Figure 2.)
The control signals are external inputs that can be fed
into the dead-time control. the error amplifier inputs,
or the feedback input. The dead-time control comparator has an effective 120 mV input offset which limits
the minimum output dead time to approximately the
first 4% of the sawtooth-cYcle time. This would result
in a maximum duty cycle on a given output of 96% with
the output control grounded, and 48% with it connected
to the reference line. Additional deacl time may be imposed on the output by setting the dead time-control
input to a fixed voltage, ranging between 0 to 3.3 V.
The pulse width modulator comparator provides a
means for the error amplifiers to adjust the output pulse
width from the maximum percent on-time, established
by the dead time control input, down to zero, as the
FIGURE 3 -
FUNCTIONAL TABLE
Inputs
lout
Output Function
Output
Control
Steering
Control
Grounded
Open
Single-ended P.W.M. at 01 and 02
At Vrel
Open
Push-pull operation
At Vrel
VI <0.4 V
Single-ended P.W.M. at 01 only
1
At Vrel
VI >2.4 V
Single-ended P.W.M. at 02 only
1
losc'
356
1
0.5
-
TL494, TL495
MAXIMUM RATINGS (Full operating ambient temperature range applies unless otherwise noted)
Symbol
TL494M
TL4941ITL4951
TL494CITL495C
Unit
VCC
42
42
42
V
VC1, VC2
42
42
42
V
IC1,IC2
250
250
250
mA
Amplifier Input Voltage
Vin
VCC + .03
VCC + .03
VCC + .03
V
Power Dissipation Co TA '" 45°C
PD
1000
1000
1000
mW
Rating
Power Supply Voltage
Collector Output Voltage
Collector Output Current (each transistor)
Operating Junction Temperature
TJ
150
150
150
°C
Operating Ambient Temperature Range
TA
- 55 to 125
- 25 to 85
o to 70
cc
Tstg
-65 to 150
-65 to 150
- 65 to 150
°c
Storage Temperature Range
THERMAL CHARACTERISTICS
Characteristics
Thermal Resistance, Junction to Ambient
Power Derating Factor
Derating Ambient Temperature
Symbol
J Suffix Ceramic Package
N Suffix Plastic Package
Unit
R"JA
100
80
°c/W
liRoJA
10.0
12.5
mWioC
TA
50
45
°c
RECOMMENDED OPERATING CONDITIONS
TL494ITL495
ConditionNalue
Power Supply Voltage
Collector Output Voltage
Collector Output Current (each transistor)
Symbol
Min.
Typ.
Max.
Unit
7.0
15
40
VC1, VC2
-
30
40
V
IC1,IC2
-
-
200
mA
VCC
Amplifier Input Voltage
Vin
Current Into Feedback Terminal
If.b.
V
-
VCC - 2.0
V
-
-
0.3
mA
-0.3
Reference Output Current
Iref
-
-
10
mA
Timing Resistor
RT
1.8
30
500
k!l
Timing Capacitor
CT
0.00047
0.001
10
fJ-F
fosc
1.0
40
200
kHz
Oscillator Frequency
ELECTRICAL CHARACTERISTICS (VCC ~ 15 V, fosc ~ 10 kHz unless otherwise noted.)
For typical values TA = 25"C, for minimax values TA is the operating ambient temperature range that applies unless otherwise
noted.
Characteristic
REFERENCE SECTION
Reference Voltage
(10 ~ 1.0 mAl
Vref
4.75
5.0
5.25
4.75
5.0
5.25
V
:;'Vref ('T)
-
0.2
2.0
-
1.3
2.6
%
Input Regulation
(VCC ~ 7.0 V to 40 V)
Regline
-
2.0
25
-
2.0
25
mV
Output Regulation
(10 = 1.0 mA to 10 mAl
Regload
-
3.0
15
-
3.0
15
mV
Short-Circuit Output Current
(Vrel ~ 0 V, TA = 25°C)
ISC
10
35
50
-
35
-
mA
Reference Voltage Change with Temperature
(aTA ~ Min to Max)
357
TL494, TL495
ELECTRICAL CHARACTERISTICS (VCC = 15 V, fosc = 10 kHz unless otherwise noted.)
For typical values TA
noted,
=
25'C, for min/max values TA is the operating ambient temperature range that applies unless otherwise
Characteristic
OUTPUT SECTION
Collector Off-State Current
(VCC = 40 V, VCE = 40 V)
IC(off)
-
2.0
Emitter Off-State Current
(VCC = 40 V, Vc = 40 V, VE = 0 V)
IE(off)
-
-
COllector-Emitter Saturation Voltage
Common-Emitter
(VE = 0V, IC = 200 mAl
Emitter-Follower
(VC = 15 V, IE = -200 mAl
Vsat(C)
-
Vsat(E)
100
-
2.0
-150
-
1.1
1.5
-
1.5
10CL
-
lOCH
Output Voltage Rise Time (TA = 25'C)
Common-Emitter (See Figure 13)
Emitter-Follower (See Figure 14)
tr
Output Voltage Fall Time (TA = 25'C)
Common-Emitter (See Figure 13)
Emitter-Follower (See Figure 14)
tf
Output Control Pin Current
Low State
(VOC '" 0.4 V)
High State
(VOC = Vref)
100
flA
-
-100
flA
-
1.1
1.3
V
2.5
--
1.5
2.5
V
10
-
-
10
-
flA
-
0.2
3,5
-
0.2
3.5
mA
-
100
200
-
100
200
ns
-
100
200
-
100
200
ns
-
25
100
-
25
100
ns
-
40
100
-
40
100
ns
TL494ITL495
Characteristic
Min
Typ
Max
ERROR AMPLIFIER SECTIONS
Input Offset Voltage
(Va (Pin 3) = 2.5 V)
Via
-
2,0
10
mV
Input Offset Current
(Va (Pin 3) = 2,5 V)
110
-
5.0
250
nA
Input Bias Current
(Va (Pin 3) = 2.5 V)
liB
-
0.1
1.0
flA
-
VCC - 2.0
V
Input Common-Mode Voltage Range
(VCC = 7.0 V to 40 V)
VICR
-0.3
Open-Loop Voltage Gain
(aVO = 3.0 V, Va = 0.5 to 3,5 V,
RL = 2.0 k!l)
AVOL
70
95
-
dB
Unity-Gain Crossover Frequency
(Va = 0.5 to 3.5 V, RL = 2.0 kH)
fC
-
350
-
kHz
Phase Margin at Unity-Gain
(Va = 0.5 to 3.5 V, RL = 2,0 kH)
0m
-
65
-
deg.
Common-Mode Rejection Ratio
(VCC = 40 V)
CMRR
65
90
Power Supply Rejection Ratio
(aVCC = 33 V, Va = 2,5 V, RL = 2,0 kH)
PSRR
-
100
-
dB
Output Sink Current
(Va (Pin 3) = 0.7 V)
10-
0.3
0,7
-
mA
Output Source Current
(Va (Pin 3) = 3,5 V)
10+
-2.0
-4,0
-
mA
358
dB
TL494, TL495
ELECTRICAL CHARACTERISTICS (VCC = 15 V, fosc = 10 kHz unless otherwise noted.)
For typical values TA = 25"C, for minimax values TA is the operating ambient temperature range that applies unless otherwise
noted.
Characteristic
PWM COMPARATOR SECTION (Test Circuit Figure 12)
Input Threshold Voltage
(Zero duty cycle)
VTH
-
3.5
4.5
Input Sink Current
(V (Pin 3) = 0.7 V)
11-
0.3
0.7
-
-
- 2.0
-10
45
-
48
45
50
50
0
2.8
-
3.3
-
losc
-
40
-
kHz
ufos c
-
3.0
-
%
Frequency Change with Voltage
(VCC = 7.0 V to 40 V, TA = 25°C)
.llosc ('V)
-
0.1
-
""
Frequency Change with Temperature
.llosc (,T)
-
1.0
2.0
","
Input Current Low
(V (Pin 13) = 0.4 V)
ISTL
-
- 200
fJ-A
Input Current High
(V(Pin 13) = 2.4 V)
(V(Pin 13) = Vrel)
ISTH
V
rnA
DEAD-TIME CONTROL SECTION (Test Circuit Figure 12)
Input Bias Current (Pin 4)
(Vin = 0 to 5.25 V)
liB (DT)
Maximum Duty Cycle, Each Output, Push-Pull Mode
(Vin = 0 V, CT = 0.1 fJ-F, RT = 12 kO)
(Vin = 0 V, CT = 0.001 fJ-F, RT = 30 kO)
DC max
Input Threshold Voltage (Pin 4)
(Zero Duty Cycle)
(Maximum Duty Cycle)
fJ-A
%
V
VTH
OSCILLATOR SECTION
Frequency
(CT = 0.001 fJ-f, RT = 30 kO)
Standard Deviation of Frequency'
(CT = 0.001 fJ-f, RT = 30 kO)
(aTA = 25"C to TA low, 25"C to TA high)
Characteristic
STEERING CONTROL
25
fJ-A
-
25
75
200
-
ZENER CHARACTERISTICS
Zener Breakdown Voltage
(IZ = 2rnA)
Vz
-
39
-
V
Sink Current
(V(Pin 15)
IRZ
-
0.3
-
rnA
=
1.0 V)
TOTAL DEVICE
Standby Supply Current
(Pin 6 at Vrel, All Other Inputs and Outputs Open)
(VCC = 15 V)
(VCC = 40 V)
ICC
Average Supply Current
IV(Pin 4) = 2.0 V) (See Figure 12.)
(CT = O.Q1,RT = 12kll,VCC = 15V)
-
rnA
-
5.5
7.0
10
15
-
7.0
-
.. Standard deviation is a measure of the statistical distribution about the mean as derived from the formula,
(1
::=
N
2:
IX n - ><12
n = 1
N - 1
359
rnA
TL494, TL495
FIGURE 4 - OSCILLATOR FREQUENCY
VERSUS TIMING RESISTANCE
FIGURE 5 -
300k
OPEN LOOP VOLTAGE GAIN AND PHASE
VERSUS FREQUENCY
100
15V'
VCC
I'-..
0
C'r ~ 0
0
~
.0'1<1'
k
f:!..I
120
15
VOC ~ Vref
V
5
.1
"'"
"-
V
o5
200
-- f-- - -
6
-- I---
o
250
50
100
."--
150
'C, COLLECTOR CURRENT [mAl
IE, EMlffiR CURRENT [mAl
360
~
<{
""""- '"
50
9r-I-~CC I~ II~J
ffi
e
100 iE
FIGURE 7 - PERCENT DUTY CYCLE VERSUS
DEAD-TIME CONTROL VOLTAGE
0
3
0
Ik
10 k
f, FREOUENCY [Hzl
RT, TIMING RESISTANCE [ill
4
-'"
0
101<1'
-20
0
0
100
2
0
200
250
TL494, TL495
FIGURE 10 - STANDBY-SUPPLY CURRENT
VERSUS SUPPLY VOLTAGE
8.0
7.0
_
~
I
a>-
5. 0
I
4. 0
II
-
~
i;1
3.0
~
2. 0
1.0
0
FIGURE 11 -
-
6.0
,.../
~
/
L
/
5.0
10
15
20
25
Vee. SUrPLYVOLTAGE IV)
ERROR AMPLIFIER CHARACTERISTICS
30
FIGURE 12 -
35
40
DEAD-TIME AND FEEDBACK CONTROL
TEST CIRCUIT
Vcc
~
1SV t - - - - -.....- - ,
ISO
2W
ISO
2W
VCC
Tesl
Inputs
~
Dead Time
Cl
El
Output 1
C2
Output 2
Feedback
Feedback
RT
Terminal
(Pin 3)
~'l
E2
(-)
(+)
Error
H
10pen)} TL49S
10pen)
Vz
Ref
Oul
Oulpul
Control
SOk
Steering
Control
Gnd
FIGURE 13 - COMMON-EMITTER CONFIGURATION
TEST CIRCUIT AND WAVEFORM
FIGURE 14 - EMITTER-FOLLOWER CONFIGURATION
TEST CIRCUIT AND WAVEFORM
ISV
1SV
Each
Output
Transistor
I
CL
1S
PF
--90%
361
Only
TL494, TL495
FIGURE 15 -
ERROR-AMPLIFIER SENSING TECHNIQUES
Vref
Vo
To Output
Voltage of
System
Rl
R2
Rl
NEGATIVE OUTPUT VOLTAGE
Vref
R1
Vo ~ - Vref112
2
Vo
POSITIVE OUTPUT VOLTAGE
R2
Vo
FIGURE 16 -
~
Vref (1
+~)
To Output
Voltage of
System
FIGURE 17 -
DEAD-TIME CONTROL CIRCUIT
SOFT-START CIRCUIT
Output
Control 0 - - - 0 - - - - - ,
Output
Vref
a
T
Vref
Ou tput
4
0--
DT
a
+
Rl
;
Cs
4
DT
R2
6
30 k
Max % on
Tim~.
1°.001
Each Output = 45- (
80 Rl)
1 + R2
FIGURE 18 -
OUTPUT CONNECTIONS FOR SINGLE-ENDED AND
PUSH-PULL CONFIGURATIONS
Cl
C,
Oc
0,
Output
Control
2.4 V '" VOC '" Vref
El
E500mA
0,
02
~0250 mA
C2
C2
0", VOC '" 0.4 V
E'
Output
Control
02
E2
E2
OE
Push-Pull Configuration
Single Ended Configuration
362
Go 250 rnA
TL494, TL495
FIGURE 19 -
FIGURE 20 - OPERATION WITH VIN > 40 V USING
INTERNAL ZENER (Tl495 ONLV)
SLAVING TWO OR MORE CONTROL CIRCUITS
Vref
RS
VCC
Master
Slave
(Additional
Circuits)
FIGURE 21 -
PULSE-WIDTH MODULATED PUSH-PULL CONVERTER
+Vin = 8.0 to 20 V
12
~+
47
VCC
r---:-:-:'--"l2 -
C, :, :
1M
33k
3
e-if-JINI.....---i Comp
0.01 0.01
15
~;" ~r-r-vt-~-Lr~1
C2
OC Vref
13
--' \....J
-;~-V-~+2:-+--O
-41"\....--+...
TL494
I-
16
,.-- +
+VO=28V
10 = 0.2 A
IN4934
141+
DT CT
.4
32 25V
RT Gnd
1
4.7k
-
47
7
-Dr-
6
4.7 k
10
10 k
4.7 k
'1'
'""""---1_VVV-_
IN4934
1
240
15k
0.101
0--1
J
All capacitors in J.l.F
L1 T1 -
3.5 mh (C, O.3A
Primary: 20T C.T. #28 AWG
Secondary: 120T C.T. #36 AWG
Core: Ferroxcube 1408P-LOO-3C8
TEST
CONDITIONS
RESULTS
Line Regulation
Yin = 8.0 to 20 V
3.0 mV
0.01%
Load Regulation
Yin = 12.6 V, 10 = 0.2 to 200 mA
5.0 mV
0.02%
Output Ripple
Yin = 12.6 V, 10 = 200 mA
Short Circuit Current
Yin = 12.6 V, RL = 0.1
Efficiency
Yin = 12.6 V, 10 = 200 mA
n
363
40 mV pop
P.A.R.D.
250 mA
72%
+
50
'
35 V
TL494, TL495
FIGURE 22 +Vin
~
PULSE·WIDTH MODULATED STEp·DOWN CONVERTER
, 1.0 mH (ii 2A
10t040V
+VO
TIP 32A
~
5.0 V
,..,......"...
~
V
10
47
150
srq
12
Cl
VCC
47 k
0.1£:
3
1M
C2 Comp
2
50
5 V
°
+
+
TL494
:Of'
Vref
CT
5
)
6
:>
14 1 13
7
14
....,
15
16 ~
+~
D.T. O.C. Gnd El E2
RT
5.1 k
5.1 k
1
MR850
500 "
10 V
+
5,1 k
+
91 10
150
47
k
0.001
Il
All capacitors in flF
TEST
CONDITIONS
Line Regulation
Yin
~
10V to 40V
Load Regulation
Yin
~
28V. 10
~
1 mA to 1 A
Output Ripple
Yin
~
28V. 10
~
1,OA
Short Circuit Current
Yin
~
28V. RL
~
0,1ll
Efficiency
Yin
~
28V. 10
~
lA
364
RESULTS
14mV
0,28%
3.0mV
0,06%
65mV p.p
P.A.RD.
1,6 amps
71%
50
f'10 V
~
1.0A
®
JLA78S40
MOTOROLA
Advance Information
UNIVERSAL
SWITCHING REGULATOR
SUBSYSTEM
UNIVERSAL SWITCHING REGULATOR SUBSYSTEM
The I'A78S40 is a monolithic-switching regulator subsystem,
providing all active functions necessary for a switching regulator
system. The device consists of a tight-tolera nce temperaturecompensated voltage reference, controlled-duty cycle oscillator
with an active peak-current limit circuit, comparator, high-current
and high-voltage output switch, capable of 1.5 A and 40 V, pinnedout power diode and an uncommitted operational amplifier, which
can be powered up or down independent of the I.C. supply. The
switching output can drive external NPN or PNP transistors when
voltages greater than 40 V, or currents in excess of 1.5 A. are
required. Some of the features are wide-supply voltage range, low
standby current, high efficiency and low drift. The I'A78S40 is
available in both commercial (OOC to +70°C) and military (-55°C to
+125°CI temperature ranges.
Some of the applications include use in step-up, step-down, and
inverting regulators, with extremely good results obtained in
battery-operated systems.
•
SILICON MONOLITHIC
INTEGRATED CIRCUIT
P SUFFIX
PLASTIC PACKAGE
CASE64B
D SUFFIX
CERAMIC PACKAGE
CASE 620
Output Adjustable from 1.3 V to 40 V
• Peak Output Current of 1.5 A Without External Transistor
• 80 dB Line and Load Regulation
PIN CONNECTIONS
•
Operation from 2.5 V to 40 V Supply
•
Low Standby Current Drain
•
High Gain, High Output Current, Uncommitted Op Amp.
• Uncommitted Power Diode
• Low Cost
Comparator
~put
I
Diode
Anode
Driver
Collector
SWitch
Emitter
Ipk Sense
VCC
Timing
Capacttor
VCC
(OpAmp)
Comparator
Inverting
Input
SWitch
Collector
OpAmp
Output
I'A7BS40 EQUIVALENT CIRCUIT
Non.lnverting
Diode
Cathode
Timing
Ipk
Capacitor Sense
9 10
Driver
VCC
OpAmp
Non-Inverting
Input
Switch
Collector Collector
Ground
Comparator
Inverting
Input
OpAmp
Inverting
Input
16
Comparator
Non-Inverting
Reference
Input
3
Switch
Emitter
Reference
;I
OpAmp
Inverting
Input
t
VCC
Op Amp Ground Diode Diode
(Op Amp) Output
Cathode Anode
OpAmp
Non-Inverting
Input
365
ORDERING INFORMATION
Temperatur.
eevice
Range
Package
aoc to +70o C
pA78540PC
Plastic DIP
pA78540DC
ODe to+70DC
Ceramic DIP
pA78540DM
-55DC to +125DC
Ceramic DIP
ILA78S40
MAXIMUM RATINGS
Rating
Power Supply Voltage
Op Amp Power Supply Voltage
Common Mode Input Range
(Comparator and Op Amp)
Differential Input Voltage (Note 2)
Symbol
Value
VCC
40
V
VCC(OpAmp)
40
V
VICR
-0.3 to VCC
V
Unit
VID
±30
V
Output Short-Circuit Duration (Op Amp)
-
Continuous
-
Reference Output Current
Iref
10
mA
Voltage from Switch Collectors to G nd
-
40
V
40
V
40
V
Voltage from Switch Emitters to Gnd
Voltage from Switch Collectors to Emitter
Voltage from Power Diode to Gnd
40
V
V
Reverse-Power Diode Voltage
VDR
40
Current through Power Switch
Isw
1.5
A
10
1.5
A
Po
1/ROJA
1500
14
1000
8
mW
mW/oC
mW
mW/OC
Tstg
-65 to +150
°c
TA
-55 to +125
to +70
°c
Current through Power Diode
Power Dissipation and Thermal Characteristics
Plastic Package - TA = +25°C
Derate above +25°C (Note 1)
Ceramic Package - TA = 25°C
Derate above +25°C (Note 1)
Storage Temperature Range
1/ROJA
PD
Operating Temperature Range
I'A78S40M
I'A78S40C
o
Notes:
1. Tlow = -55°e for ~A78S40DM
= ooe for ~A78S40De and ~A78S40pe
Thigh = +125°e for ~A78S40DM
= +70oe for ~A78S40De and ~A78S40pe
2. For supply voltages less than 30 V the maximum differential input voltage (Error Amp and Op Amp)
is equal to the supply voltage.
ELECTRICAL CHARACTERISTICS (VCC = 5.0 V. VCC (Op Amp) = 5.0 V, TA = Tlow to Thigh unless otherwise noted.)
Characteristic
GENERAL
Supply Voltage
VCC
2.5
-
40
V
Supply Current (Op Amp Disconnected)
(VCC= 5.0V)
(VCC= 40V)
ICC
-
1.8
2.3
3.5
5.0
mA
Supply Current (Op Amp Connected)
(VCC = 5.0V)
(VCC= 40 V)
ICC
-
-
4.0
5.5
mA
1.245
1.310
V
-
REFERENCE
Reference Voltage
(Iref = 1.0 mAl
Vref
1.180
Reference Voltage Line Regulation
(3.0 V.;; VCC';; 40 V, Iref = 1.0 mA. TA = 25°C)
RegLine
-
0.04
0.2
mV/V
Reference Voltage Load Regulation
(1.0 mA';; Iref';; 10 mA, TA = 25°C)
RegLoad
-
0.2
0.5
mV/mA
366
fl.A78S40
ELECTRICAL CHARACTERISTICS (Continued)
Characteristic
OSCILLATOR
Charging Current (TA = 25°C)
(VCC= 5.0V)
(VCC = 40 V)
Ichg
Discharge Current (TA = 25°C)
(VCC= 5.0V)
(VCC = 40 V)
Ichg
Oscillator Voltage Swing (TA = 25°C)
(VCC= 5.0V)
Vosc
-
0.5
-
V
ton/toff
-
6.0
-
iJ.s/iJ.S
Output Saturation Voltage 1
(ISW = 1.0 A, Pin 15 tied to Pin 16)
Vsat1
-
1.1
1.3
V
Output Saturation Voltage 2
(ISW = 1.0 A, 115 = 50 mAl
Vsat2
-
0.45
0.7
V
hFE
-
70
-
-
-
-
10
-
nA
Input Offset Voltage (VCM = Vref)
Via
15
mV
liB
35
200
nA
Input Offset Current (VCM = Vrefl
110
-
1.5
Input Bias Current (VCM = Vrefl
5.0
75
nA
Common-Mode Voltage Range (TA = 25°C)
VICR
0
-
Power-Supply Rejection Ratio (TA = 25°C)
(3.0";VCC,,;40V)
PSRR
70
96
Input Ofset Voltage IVCM = 2.5 V)
Via
Input Bias Current (VCM = 2.5 V)
liB
Input Offset Current (VCM = 2.5 V)
110
-
Voltage Gain + (TA = 25°C)
(RL = 2.0 kn to Gnd, 1.0 V"; Va"; 2.5 V)
Avol+
Voltage Gain - (TA = 25°C)
(RL = 2.0 kn to VCC (op amp), 1.0 V"; Va"; 2.5 V)
Turn-on/Turn-off
20
20
150
150
-
-
-
iJ. A
50
70
iJ. A
250
350
CURRENT LIMIT
Current-Limit Sense Voltage (TA = 25°C)
(VCC - VIPK [Sensell
OUTPUT SWITCH
Output Transistor Current Gain (TA = 25°C)
(IC = 1.0 A, VCE = 5.0 V)
Output Leakage Current (TA = 25°C)
(VO=40V)
POWER DIODE
Forward Voltage Drop (10 = 1.0 A)
Diode Leakage Current (TA = 25°C) (VOR = 40 V)
COMPARATOR
VCC-2
V
-
dB
4.0
15
mV
30
200
nA
5.0
75
nA
25000
250000
-
VIV
Avol-
25000
250000
-
VIV
Common-Mode Voltage Range (TA = 25°C)
VICR
,0
-
VCC-2
V
Common-Mode Rejection Ratio (TA = 25°C)
(VCM = 0 to 3.0 V)
CMRR
76
100
-
dB
Power-Supply Rejection Ratio (TA = 25°C)
(3.0 V"; VCC (op amp)"; 40 V)
PSRR
76
100
-
dB
ISource
75
150
ISink
10
35
-
-
0.6
-
-
1.0
V
-
V
OUTPUT OPERATIONAL AMPLIFIER
Output Source Current (TA = 25°C)
Output Sink Current (TA = 25°C)
SR
Slew Rate (TA = 25°C)
Output Low Voltage (TA = 25°C) (lL = -5.0 mAl
VOL
Output High Voltage (TA = 25°C) (IL = 50 rnA)
!VCC (Op Amp)
-3.0V
367
mA
mA
VII's
368
SECTION 19
PACKAGE OUTLINE DIMENSIONS
LP, P, Z SUFFIX
PLASTIC PACKAGE
CASE 29-02
K SUFFIX
METAL PACKAGE
CASE 1-03
MB
K~".'"'~'j
"""'lEi
PLANE F
0
-J-
0L:6 V ~ 1
~
~ ~\ ~T I j
t
~ Y
lo
H
J
K
n
MILLIMETERS
MIN MAX
4.32
5.33
4.44
5.21
C
3.1B
4.19
D
0.41
0.56
F
0.41
0.48
G
1.14
1.40
H
2.54
J
2.41
2.67
K 12.70
L
6.35
N
2.03
2.92
P
2.92
R
3.4
S
0.41
0.36
DIM
A
INCHES
MAX
MIN
0.B75
0.450
0.250
0.043
0.038
0.135
1.177
1.197
0.440
0.420
0.105
0.125
0.655
0.675
0.311
0.151
0.161
0.515
0.188
-
T
L
!
~
rI
"-S
G
--------r
Dj~
\;-
DIM
B
C
0
E
F
-
K
:----- F -
MILLIMETERS
MIN
MAX
22.13
6.35 11.43
0.97
1.09
3.43
19.90 30.40
10.67 11.1B
5.11
5.72
16.64 17.15
7.92
3.84
4.09
13.34
4.78
A
•
-
All JEDEC dimensIOns and notes applv
INCHES
MIN MAX
0.170 0.210
0.175 0.205
0.125 0.165
0.016 0.022
0.016 0.019
0.045 0.05
0.100
0.095 0.105
0.500
0.20
O. 80 0.115
0.115
-
-
.I~li
0.014
SECT.A·A
~'
1:
N
NOTES.
1. CONTOUR OF PACKAGE BEYOND ZONE "P"
IS UNCONTROLLED.
2. DIM "F" APPLIES BETWEEN "H" AND
"L". Dlr,\ "0" & "S" APPLIES BETWEEN
"L" & 12.70 mm 10.5") FROM SEATING
PLANE. LEAD DIM IS UNCONTROLLED
IN "H" & BEYOND 12.70 mm 10.5")
FROM SEATING PLANE.
0.016
All JEDEC dimensions and notes apply.
G, H SUFFIX
METAL PACKAGE
CASE 79-02
R SUFFIX
METAL PACKAGE
CASE 80-02
--u--
•
re- --
P
4-
L
~K
------=.l
H
MILLIMETERS
DIM MIN MAX
A
8.89 9.40
B
8.00 8.51
C
6.10 6.60
D
0.406 0.533
E
0.229 3.18
F
0.406 0.483
G
4.83 5.33
H
0.711 0.B64
J
0.737 1.01
K 12.70
L
6.35
M
450 NOM
P
1.27
n
R
900 NOM
2.54
v-: ~
~•
N
X¥J
M
H
! "
All JEDEC dimension.
and notes apply.
1
1
l-
1
~
~
)(.T
~
~
MILLIMETERS
INCHES
MIN MAX MIN
MAX
11.94 11.70 0.470 0.500
6.35 8.64 0.150 0.340
0.71
0.86 0.018 0.034
1.27
1.91 0.050 0.075
24.33 24.43
0.95B 0.961
4.83
5.33 0.190 0.110
1.41
1.67
0.095 0.105
14.48 14.99 0.570 0.590
9.14
0.360
1.17
0.050
Q
3.61
3.86 0.141 0.152
S
8.89
0.350
T
3.68'
0.145
U
15.75
0.610
AI, JEDEC Dimensions and and Notes Apply.
INCHES
MIN MAX
1 0.370
I 0.335
I 0.260
1 0.021
I 0.125
DIM
B
C
0
E
F
G
H
J
K
P
~
~
1 0.034
1 0.040
-
~
r--J-
O~'
\.
(v,1
~~,.
C
-------
SEA:)G PLANE/t D
r------F--
SE:L~~ ~'--D
/
-B--
369
-
-
PACKAGE OUTLINE DIMENSIONS (continued)
T SUFFIX
PLASTIC PACKAGE
CASE 221A-02
C
a
F
4.06
0.64
3.61
4.82
0.89
3.73
0.160
0.025
0.142
~
l:~~
g~ ~n~ ~:~~
J
0.36
0.56
0.014
G SUFFIX
METAL PACKAGE
CASE 603-04
aiM
A
B
C
0.190
0.035
0.147
0.022
f-;~+I~~'f:'!-~+,,1~~:lg~+'~~:~~~::C+-~~:~~:~;--1
o
NOTES
1. DIMENSIONS LAND H APPL1ESTO AU LEADS.
t
2.
~6~~N1~ODN LZE~~~'::~GAU i~~iT~:SE::
~~+-'1~"!:~'!-~+c~~:~~~+.~~:",~~~~~:~g'*~--1
3.
~~~~:S~~NING AND TOLERANCING PER ANSI
p.;'+~;"':~7:+c~~i~:-H~c;:~"'::~*,~:*,:;"F:-1
4.
~:~~~~7(LING DIMENSION, INCH
T
5.97
6.48
0.235
0.255
U
0.76
1.14
1.27
0.030
0.045
0.050
V
z
2.03
MILLIMETERS
MIN MAX
8.51
9.39
7.75
8.51
4.19
4.70
0.407 0.533
INCHES
MIN
MAX
0.335 0.370
0.305 0.335
0.165 0.185
0.016 0.011
E
F
G
0.406 1.021.040
0.483
0.019
5.848SC
BSC
0.712 0.864
0.034
J
0.737 1.14
0.045
K 11.70
L 6.35 12.70
0.500
M
36" BSC
BSC
P
1.27
0.050
a 3.56 4.06 0.140 0.160
R 0.254 1.02 0.010 0.040
H
L
NOTE,
LEADS WITHIN 0.18 mm 10.007) RADIUS OF
TR UE POSITION AT SEATING PLANE
AT MAXIMUM MATERIAL CONDITION.
All JEDEG dimensIOns and notes apply
0.080
R SUFFIX
METAL PACKAGE
CASE 614-02
G SUFFIX
METAL PACKAGE
CASE 603C-01
~:~4etIC
r,;-t]---tL
L111
P
_ _ _ ~jK
SEATING
PLANE
--il--D
rrol~o./'M
G
,..---,------,--,-CC,NCCCCCHCCESC-..., .
MILLIMETERS
DIM
A
B
C
0
E
MIN
8.51
6.73
0.335
0.305
0.165
0.407
0.533
0.016
-
1.02
H
0.712 0.864
0.737 1.14
1270
-
Q
R
0.370
0.335
0.265
775
4.19
0.406 0.483
L
M
P
MAX
8.51
F
G
J
K
MIN
MAX
939
5.84 Bse
6.35 11.70
36° Bse
1.27
3.56 4.06
0.154 1.01
0021
-
0.040
0.016
0.019
0.230 Bse
0.018
0.019
0.500
0.150
0.034
0.045
Q
J~ o(::)io~
V
0
09
870
0
"- H
DIM
A
B
C
NOTES,
o
1. LEADS WITHIN 0.18
mm (0,007) RADIUS
OF TRUE POSITION TO DIM. "AU & "H"
AT SEATING PLANE AT MAXIMUM
MATERIAL CONDITION.
E
F
G
2. LEAD DIA UNCONTROLLED BEYONO
0.500
H
DIM "K" MIN.
J
K
36° Bse
0.050
0.140
0160
O.OlD
0.040
P
a
R
370
MIlliMETERS
INCHES
MIN MAX
MIN MAX
31.80
1.251
11.94 12.70 0.470 0.500
6.35
8.64 0.150 0.340
0.71
0.81 0.028 0.032
1.27
1.90 0.050 0.D75
36° BSC
360 BSG
8.26 BSC
0.325 BS
14.33 24.43 0.95B 0.962
12.17 12.22 0.479 0.481
9.14
0.360
1.40 BSC
0.055 BSC
3.61
3.86 0.141 0.152
17.78
0.700
NOTE,
1. LEADS TRUE POSITIONED
WITHIN 0.36 mm (0.014) OIA. to DIM.
"A" & "H" AT MAX. MATERIAL
CONDITIONS AND DIM. "P"
2. LEAD DIAMETERS ARE UNCON·
TROLLED BEYOND 11.70 mm 10.500)
FROM BASE PLANE.
PACKAGE OUTLINE DIMENSIONS (continued)
P, P1 SUFFIX
PLASTIC PACKAGE
CASE 626-04
0, J, L SUFFIX
CERAMIC PACKAGE
CASE 620-02
0
Ol
1
P
,~
1
t
G
H
J
K
L
M
N
MILLIMETERS
MIN
MAX
19.05
8.22
4.06
0.38
1.40
2.54
0.51
0.20
3.18
.3
-
0.51
19.81
6.98
5.08
0.51
1.65
SSC
1.14
0.30
4.06
7.87
15'
1.02
INCHES
MIN
MAX
0.750 0.780
0.245 0.275
0.160 0.200
0.015 0.020
0.05
0.065
0.100 BSC
0.020 0.045
O. 08 0.012
0.125 0.180
0.290 0.310
15·
0.020 0.040
,-.
DIM
NOTES,
1 LEAOS WITHIN 0.13 mm 10.005) RAOIUS
OFTRUE POSITION AT SEATING PLANE
AT MAXIMUM MATERIAL CONOITION
2 PKG.INOEX, NOTCH IN LEAO
NOTCH IN CERAMIC OR INK OOT
301M T' TO CENTER Of LEADS
WHEN fORMED PARALLEL
A
B
C
D
F
G
H
J
K
L
M
N
MILLIMETERS
MIN
MAX
9.40 10.16
6.10
6.60
3.94
4.45
0.38
0.51
1.02
1.52
2.546SC
0.76
1.27
0.20
0.30
2.92
3.43
7.626SC
10'
0.51
0.76
L SUFFIX
CERAMIC PACKAGE
CASE 632-02
Q1
~~DJ
NOTES,
1. LEAOS WITHIN 0.13 mm
10.005) RAOIUS Of TRUE
POSITION AT SEATING
PLANE AT MAXIMUM
MATERIAL CONOITION.
2. DIM "L"TO CENTER Of
LEADS WHEN fORMED
PARALLEL
3. PACKAGE CONTOUR
OPTIONAL IROUNO OR
SQUARE CORNERS)
-
AAAAAAA
I
"
QJ 0
P
F
r- A~--.l
INCHES
MAX
MIN
0.370 0.400
0.240 0.260
0.155 0.175
0.015 0.020
0.040 0.060
0.1008SC
0.030 0.050
0.008 0.012
0.115 0.135
0.3006SC
10'
0.020 0.030
P SUFFIX
PLASTIC PACKAGE
CASE 646-05
7~
1
B
~~b~~
PLANE
A
8
C
D
F
J
---I FI-
~n
tL~~,~
. _-J
DIM
A~
NOTE 3
r--'~['1
.
~AV
'11
' -.i
v VI
Note 4
;;-r r.L~
1C
fflMM
FitJL
_ f- -i l- -i~SEATING
J
M-1C~
--jFr-
I-L
JH~~G~ SEA:~NG t~ MJ~\\--
H
G
DPLANE
K
M
PLANE
MILLIMETERS
DIM MIN MAX
A 16.8
19.9
B
5.59
7.11
C
5.08
0
0.381 0.584
F
0.77
1.77
2.54 6SC
J
0.203 0.381
K 2.54
L
7.628SC
M
15'
N
0.51
0.76
P
8.25
-
-
INCHES
MIN
MAX
0.660 0.785
0.220 0.280
0.200
0.015 0.023
0.030 0.070
0.1006SC
0.008 0.015
0.100
0.3006SC
15'
0.020 0.030
0.325
' NOTES,
1. ALL RULES AND NOTES ASSOCIATED
WITH MO·OOl AA OUTLINE SHALL APPLY.
2. DIMENSION "L"TO CENTER Of LEADS
WHEN fORMED PARALLEL.
3. LEADS WITHIN 0.25mm 10.010) OIA Of TRUE
POSITION AT SEATING PLANE AND MAXIMUM
MATERII'L CONDITION.
All JEDEC dimensions and notes apply.
371
MILLIMETERS
DIM MIN
MAX
A 18.16 19.56
6.10
6.60
B
5.08
C
4.06
0.38
0.53
0
F
1.02
1.78
.54l1S1
G
H
1.32
2.41
I
0.20
0.38
.9
K
3.43
7.626SC
L
M
0
10'
N
0.51
1.02
INCHES
MIN MAX
0.715 0.770
0.240 0.260
0.160 0.200
0.015 0.021
0.040 0.070
0.101 lISe0.095
0.05
0.008 0.015
0.115 0.135
0.30 8 C
100
0
0.020 0.040
NOTES,
1. LEAOS WITHIN 0.13 mm
10.005) RADIUS Of TRUE
POSITION AT SEATING
PLANE AT MAXIMUM
MATERIAL CONOITION.
2. DIMENSION "L" TO
CENTER Of LEADS
WHEN FORMED
PARALLEL.
3. DIMENSION "6" DOES NOT
INCLUDE MOLD fLASH.
4. ROUNDED CORNERS OPTIONAL
PACKAGE OUTLINE DIMENSIONS (continued)
JG, U SUFFIX
CERAMIC PACKAGE
CASE 693-02
N, P SUFFIX
PLASTIC PACKAGE
CASE 648-05
OPTIONAL LEAD
CON FIG. 11.8,9,& 16)
H~ ~
..,~TE5
~,
G
MILLIMETERS
OIM MIN
MAX
A 18.80 21.34
6.10
6.6
c 4.06 5.08
0
0.38
0.53
F
1.02
1.78
2.54 asc
G
H
0.38
2.41
J
J8
0.20
.2
3.43
L
7.62 ase
100
0
M
N 0.51
1.02
f--
JLD
r:= =J
f.1
\'TI.: J
,.--_ _ _ _ _ _ _ _
J
PLANE
--I
L
J
M
NOTES:
1. LEADSWITHINO.13mm
10.0051 RADIUS OF TRUE
POSITION AT SEATING
PLANE AT MAXIMUM
MATERIAL CONDITION.
2. DIMENSION "L" TO
CENTER OF LEADS
WHEN FORMED
PARALLEL.
3. DIMENSION "8" DOES NOT
INCLUDE MOLD FLASH.
4. "F" DIMENSION IS FOR FULL
LEADS. "HALF" LEADS ARE
OPTIONALATLEAD POSITiONS
1,8,S,end 161.
5. ROUNDED CORNERS OPTIONAL.
NOTES:
1. LEADS WITHIN 0.13 mm 10.0051
RAD OF TRUE POSITION AT
SEATING PLANE AT MAXIMUM
MATERIAL CONDITION.
2. DIMENSION "L" TO CENTER
OF LEADS WHEN FORMED
PARALLEL.
DIM
A
a
C
D
F
G
H
J
K
L
M
N
0.51
N SUFFIX
PLASTIC PACKAGE
CASE 707-02
MILLIMETERS
DIM MIN
MAX
A 22.22 23.24
a 6.10 6.60
3.56
C
4.57
D
0.36
0.56
1.27
1.78
F
2.54 BSC
G
1.52
1.02
H
0.20
0.30
J
K
2.S2
3.43
L
7.62 BSC
00
15 0
M
N
0.51
1.02
NOTES:
1. POSITIONAL TOLERANCE OF LEADS (D).
SHAll BE WITHIN 0.25mm(0.010) AT
MAXIMUM MATERIAL CONDITION, IN
RELATION TO SEATING PLANE AND
EACH OTHER.
2. DIMENSiON L TO CENTER OF LEADS
WHEN FORMED PARALLEL.
3. DIMENSION B ODES NOT INCLUDE
MOLD FLASH.
372
INCHES
MIN
MAX
0.875 0.S15
0.240 0.260
0.140 0.180
0.014 0.022
0.05
0.070
0.100 BSC
0.040 0.060
0.008 0.012
0.115 0.135
O. 00 BSC
()O
150
0.020 0.040
PACKAGE OUTLINE DIMENSIONS (continued)
J SUFFIX
D SUFFIX
CERAMIC PACKAGE
PLASTIC PACKAGE
CASE 7S1A-01
[G:::::::J:5JL~n::
,
-I
I
-1G~
A
~~
Jul"JL,iC~
DIM MIN
A 22.35
B
6.63
e
o
F
G
H
J
K
L
M
N
MAX
23.11
7.24
5.0B
0.51
1.65
0.41
1.40
2.54 Bse
0.76
1.02
0.13
0.38
4.44
7.37
B.OO
00
150
0.51
0.76
NOTES:
1. LEADS, TRUE POSITIONED
WITHIN 0.25 mm 10.010) DIA.
AT SEATING PLANE, AT
MAXIMUM MATERIAL
CONDITION.
DIM
A
B
e
2. DIM "L"TD CENTER OF
LEADS WHEN FD RMED
PARALLEL.
0
F
G
J
K
3. DIM "A" & ''8'' INCLUDES
MENISCUS.
L
P
373
MILLIMETERS
INCHES
MIN MAX
MIN MAX
B.54
B.74
0.336 0.344
4.01
3.Bl
0.150~
1.35
1.75
~
0.35
0.46
~
0.67
0.77
~
1.27 BSC
~
0.19
0.22
~
0.10
0.20
~
5.21
4.B2
~
.79
6.20
.J!Mi.
NOTES:
1. ·T· IS SEATING PLANE.
2. DIMENSION A IS DATUM.
3. POSITIONAL TOLERANCE
FOR LEADS:
1... 10.2510.010) elA®1
374
SECTION 20
VOLTAGE REGULATOR
CROSS REFERENCE GUIDE
This cross reference provides a complete interchangeability list linking the
most common voltage regulators offered by major Linear Integrated Circuits
manufacturers to the nearest equivalent Motorola device. The Motorola "Direct
Replacement" column lists devices with identical pin connections and package and
the same or better electrical characteristics and temperature range. The Motorola
"Functional Equivalent" column provides a device which performs the same
function but with possible differences in package configurations, pin connections,
temperature range or electrical characteristics.
Grouped by individual manufacturers, reference numbers are listed in alphanumeric sequence, with Greek "IJ." preface numbers appearing first.
375
REFERENCE
NUMBER
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
REFERENCE
NUMBER
FAIRCHILD
...,4109KM
...,4117KM
JJ.A209KM
JJ.217UV
...,4309KC
...,4317KC
..,A317UC
...,4494DC
...,4494DM
...,4494PC
...,4723DC
...,4723DM
...,4723HC
...,4723HM
...,4723PC
...,47805KC
...,47805KM
...,47805UC
JJ.A7805UV
...,47806KC
...,47806KM
...,47806UC
JJ.A7806UV
...,47808KC
...,47808KM
...,47808UC
...,47808UV
...,47812KC
...,47812KM
...,47812UC
JJ.A7812UV
...,47815KC
...,47815KM
...,47815UC
...,47815UV
...,47818KC
...,47818KM
...,47818UC
JJ.7818UV
JJ.7824KC
...,47824KM
JJ.A7824UC
...,47824UV
...,478GKC
JJ.A78GKM
...,478GUC
...,478L05AHC
JJ.A78L05AWC
JJ.A78L08AWC
JJ.A78112AHC
...,478112AWC
...,478L15AHC
...,478115AWC
JJ.A78L18AHC
...,478L18AWC
...,478l24AHC
...,478l24AWC
...,478MGHC
...,478MGHM
...,478MGUC
...,478MOSHC
LMl09K
LMl17K
LM209K
LM217K
LM309K
LM317K
LM317T
TL494CJ
TL494MJ
TL494CN
MC1723CL
MC1723L
MC1723CG
MC1723G
MC1723CP
MC7805CK
MC7805K
MC7805CT
MC7805BT
MC7806CK
MC7806K
MC7806CT
MC7806BT
MC7808K
MC7808K
MC7808CT
MC7808BT
MC7812CK
MC7812K
MC7812CT
MC7812BT
MC7815CK
MC7815K
MC7815CT
MC7815BT
MC7818CK
MC7818K
MC7818CT
MC7818BT
MC7824CK
MC7824K
MC7824CT
MC7824BT
LM317K
LM117K
LM317T
MC78L05ACG
MC78L05ACP
MC78L08ACP
MC78L12ACG
MC78L12ACP
MC78115ACG
MC78115ACP
MC78L18ACG
MC78L18ACP
MC78l24ACG
MC78l24ACP
LM317MR
LM117MR
LM317MT
MC78M05CG
376
MOTOROLA
DIRECT
REPLACEMENT
...,478M05UC
...,478M06HC
...,478M06UC
...,478M08HC
...,478M08UC
...,478M12HC
...,478M12UC
JJ.A78M15HC
JJ.A78M15UC
...,478M24HC
...,47905KM
...,47905UC
...,47906KC
...,47906KM
...,47906UC
...,47908KC
JJ.A7908KM
...,47908UC
...,47912KC
...,47912KM
JJ.A7912UC
...,47915KC
JJ.A7915KM
JJ.A7915UC
...,47918KC
JJ.7918KM
...,47918UC
...,47924KC
...,47924KM
...,47924UC
...,479M05AUC
...,479M06AUC
...,479M08AUC
...,479M12AUC
JJ.A79M15AUC
JJ.A79M24AUC
SH323SKC
NATIONAL
MC78M05CT
MC78M06CG
MC78M06CT
MC78M08CG
MC78M08CT
MC78M12CG
MC78M12CT
LM109H
LM109K
LMl17H
LMl17K
LM120H-5.0
LM120H-12
LM120K-5.0
LM120K-12
LM120H-15
LM120K-15
LM123K
LM125H
LM126H
LM137K
LM140AK-5
LM140AK-12
LM140AK-15
LM140K-S.O
LM140K-12
LM140K-15
LM140LAH-5.0
LM140LAH-12
LM140LAH-15
LM150K
LM109H
LM109K
LMl17H
LMl17K
MOTOROLA
FUNCTIONAL
EQUIVALENT
MC78M15CG
MC78Ml5CT
MC78M24CG
MC7905CK
MC7905CT
MC7906CK
MC7906CK
MC7906CT
MC7908CT
MC7908CK
MC7908CT
MC7912CK
MC7912CK
MC7912CT
MC7915CK
MC7915CK
MC7915CT
MC7918CK
MC7918CK
MC7918CT
MC7924CK
MC7924CK
MC7924CT
MC7905CT
MC7906CT
MC7908CT
MC7912CT
MC7915CT
MC7924CT
LM323K
MC7905CK
MC7912CK
MC7905CK
MC7912CK
MC7915CK
MC7915CK
LM123K
MC1568G
MC1568G
LM137K
MC7805AK
MC7812AK
MC7815AK
LM140K-S.O
LM140K-12
LM140K-15
MC78L05ACG
MC78L12ACG
MC78L15ACG
LM1S0K
REFERENCE
NUMBER
LM209H
LM209K
LM217H
LM217K
LM223K
LM225H
LM226H
LM237K
LM250K
LM309H
LM309K
LM317H
LM317K
LM317MP
LM317T
LM320H-5.0
LM320H-12
LM320H-15
LM320K-5.0
LM320K-12
LM320K-15
LM320LZ-5.0
LM320LZ-12
LM320LZ-15
LM320T-5.0
LM320T-12
LM320T-15
LM323K
LM325AN
LM325AS
LM325G
LM325H
LM325N
LM326H
LM326N
LM326S
LM337K
LM337MP
LM337T
LM340AK-5.0
LM340AK-12
LM340AK-15
LM340AT-5.0
LM340AT-12
LM340AT-15
LM340K-5.0
LM340K-12
LM340K-15
LM340LAH-5.0
LM340LAH-12
LM340LAH-15
LM340LAZ-5.0
LM340LAZ-12
LM340LAZ-15
LM340T-5.0
LM340T-12
LM341p-5.0
LM341p-12
LM341p-15
LM342p-5.0
LM342p-12
LM342p-15
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
REFERENCE
NUMBER
LM350K
LM723CH
LM723CJ
LM723CN
LM723H
LM723J
LM7805CK
LM7805CT
LM7812CK
LM7812CT
LM7815CK
LM7815CT
LM78L05ACH
LM78L05ACZ
LM78L05CH
LM78L05CZ
LM78L12ACH
LM78L12ACZ
LM78L12CH
LM78L12CZ
LM78L15ACH
LM78L15ACZ
LM78L15CH
LM78L15CZ
LM78M05CP
LM78M12CP
LM78M15CP
LM7905CK
LM7905CT
LM7912CK
LM7912CT
LM7915CK
LM7915CT
LM79L05ACZ
LM79L12ACZ
LM79L15ACZ
LM209H
LM209K
LM217H
LM217K
LM223K
MC1568G
MC1568G
LM237K
LM250K
LM309H
LM309K
LM317H
LM317K
LM317MT
LM317T
MC7905CK
MC7912CK
MC7915CK
MC7905CK
MC7912CK
MC7915CK
MC79L05ACP
MC79L12ACP
MC79L15ACP
MC7905CT
MC7912CT
MC7915CT
LM323K
MC1468L
MC1468L
MC1468L
MC1468L
MC1468L
MC1468G
MC1468L
MC1468L
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
LM350K
MC1723CG
MC1723CL
MC1723CP
MC1723G
MC1723L
MC7805CK
MC7805CT
MC7812CK
MC7812CT
MC7815CK
LM7815CT
MC78L05ACG
MC78L05ACP
MC78L05CG
MC78L05CP
MC78L12ACG
MC78L12ACP
MC78L12CG
MC78L12CP
MC78L15ACG
MC78L15ACP
MC78L15CG
MC78L15CP
MC78M05CT
MC78M12CT
MC78M15CT
MC7905CK
MC7905CT
MC7912CK
MC7912CT
MC7915CK
MC7915CT
MC79L05ACP
MC79L12ACP
MC79L15ACP
RAYTHEON
LM337K
LM337MT
LM109H
LM209H
LM309H
RC4194DC
RC4194TK
RC4195NB
RC4195T
RC4195TK
RC723DB
RC723DC
RC723T
RM4194DC
RM4194TK
RM4195T
RM4195TK
RM723DC
RM723T
LM337T
MC7805ACK
MC7812ACK
MC7815ACK
MC7805ACT
MC7812ACT
MC7815ACT
LM340K-5.0
LM340K-12
LM340K-15
MC78L05ACG
MC78L12ACG
MC78L15ACG
MC78L05ACP
MC78L12ACP
MC78L15ACP
MC7805CT
MC7812CT
MC78M05CT
MC78M12CT
MC78M15CT
MC78M05CT
MC78M12CT
MC78M15CT
LM109H
LM209H
LM309H
MC1468L
MC1468R
MC1468L
MC1468G
MC1468R
MC1723CP
MC1723CL
MC1723CG
MC1568L
MC1568R
MC1568G
MC1568R
MC1723L
MC1723G
RCA
CA3085
CA3085A
CA3085AF
CA3085AS
CA3085B
CA3085BF
377
MC1723G
MC1723G
MC1723L
MC1723G
MC1723G
MC1723L
REFERENCE
NUMBER
CA3085BS
CA3085F
CA3085S
CA723CE
C723CT
CA723T
CA723E
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
REFERENCE
NUMBER
MC1723G
MC1723L
MC1723G
SG2501AT
SG2501J
SG2501T
SG2502J
SG2502N
SG2503M
SG2503Y
SG2503T
SG250K
SG309K
SG309P
SG309R
SG309T
SG317T
SG317R
SG317K
SG317P
SG337T
SG337R
SG337K
SG337P
SG340K-05
SG340K-06
SG340K-D8
SG340K-12
SG340K-15
SG340K-18
SG340K-24
SG3501AJ
SG3501AN
SG3501AT
SG3501J
SG3501T
SG3502J
SG3503Y
SG3503T
SG3503M
SG350K
SG3511T
SG3511J
SG3511N
SG4194CJ
SG4194J
SG4194CR
SG4194R
SG4501T
SG4501J
SG4501N
SG501AJ
SG723CJ
SG723CN
SG723CT
SG723J
SG723T
SG7805ACK
SG7805ACP
SG7805ACR
SG7805ACT
SG7805AK
SG7805AR
SG7805AT·
SG7805CK
MC1723CP
MC1723CG
MC1723G
MC1723L
SIGNETICS
JAA723F
JAA723CF
JAA723CL
,...A723CN
NE550A
NE550L
SE550L
MC1723L
MC1723CL
MC1723CG
MC1723CP
MC1723CP
MC1723CG
MC1723G
SILICON
GENERAL
SG109K
SG109R
SG109T
SG117T
SG117R
SG117K
SG123K
SG137T
SG137R
SG137K
SG140K-05
SG140K-{)6
SG140K-D8
SG140K-12
SG140K-15
SG140K-18
SG140K-24
SG1468T
SG1468R
SG1468J
SG1468N
SG150K
SG1501AJ
SG1501J
SG1501T
SG1502J
SG1503Y
SG1503T
SG1511T
SG1511J
SG1568T
SG1568R
SG1568J
SG209K
SG209R
SG209T
SG217T
SG217R
SG217K
SG223K
SG237T
SG237R
SG237K
LM109K
MC109K
LM109H
LM117H
LM117K
LM117K
LM123K
LM137H
LM137K
LM137K
LM140K-5.0
LM140K-6.0
LM140K-8.0
LM140K-12
LM140K-15
LM140K-18
LM140K-24
MC1468G
MC1468R
MC1468L
MC1468L
LM150K
MC1568L
MC1568L
MC1568G
MC1568L
MC1503U
MC1503U
MC1563G
MC1563G
MC1568G
MC1568R
MC1568L
LM209K
MC209K
LM209H
LM217H
LM217K
LM217K
LM223K
LM237H
LM237K
LM237K
378
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
MC1468L
MC1468G
MC1468L
MC1468L
MC1403AU
MC1403AU
MC1403AU
LM250K
LM309K
LM309K
MC309K
LM309H
LM317H
LM317T
LM317K
LM317T
LM337H
LM337T
LM337K
LM337T
LM340K-5.0
LM340K-6.0
LM340K-8.0
LM340K-12
LM340K-15
LM340K-18
LM340K-24
MC1468L
MC1468L
MC1468G
MC1468L
MC1468G
MC1468L
MC1403U
MC1403U
MC1403U
LM350K
MC1463G
MC1463G
MC1463G
MC1468L
MC1568L
MC1468R
MC1568R
MC1468G
MC1468L
MC1468L
MC1468G
MC1723CL
MC1723CP
MC1723CG
MC1723L
MC1723G
MC7805ACK
MC7805ACT
MC7805ACT
MC7805ACT
MC7805AK
MC7805AK
MC7805AK
MC7805CK
REFERENCE
NUMBER
SG7805CP
SG7805CR
SG7805CT
SG7805K
SG7805R
SG7805T
SG7806ACK
SG7806ACP
SG7806ACR
SG7806ACT
SG7806AK
SG7806AR
SG7806AT
SG7806CK
SG7806CP
SG7806CR
SG7806CT
SG7806K
SG7806R
SG7806T
SG7808ACK
SG7808ACP
SG7808ACR
SG7808ACT
SG7808AK
SG7808AR
SG7808AT
SG7808CK
SG7808CP
SG7808CR
SG7808CT
SG7808K
SG7808R
SG7808T
SG7812ACK
SG7812ACP
SG7812ACR
SG7812ACT
SG7812AK
SG7812AR
SG7812AT
SG7812CK
SG7812CP
SG7812CR
SG7812CT
SG7812K
SG7815ACK
SG7815ACP
SG7815ACR
SG7815ACT
SG7815AK
SG7815AR
SG7815AT
SG7815CK
SG7815CP
SG7815CR
SG7815CT
SG7815K
SG7815R
SG7815T
SG7818ACK
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
MC7805CT
REFERENCE
NUMBER
SG7818ACP
SG7818ACR
SG7818ACT
SG7818AK
SG7818AR
SG7818AT
SG7818CK
SG7818CP
SG7818CR
SG7818CT
SG7818K
SG7818R
SG7818T
SG7824ACK
SG7824ACP
SG7824ACR
SG7824ACT
SG7824AK
SG7824AR
SG7824AT
SG7824CK
SG7824CP
SG7824CR
SG7824CT
SG7824K
SG7824R
SG7824T
SG7905ACK
SG7905ACP
SG7905ACR
SG7905ACT
SG7905CK
SG7905CP
SG7905CR
SG7905CT
SG7905.2CK
SG7905.2CP
SG7905.2CR
SG7905.2CT
SG7908CK
SG7908CP
SG7908CR
SG7908CT
SG7912ACK
SG7912ACP
SG7912ACR
SG7912ACT
SG7912CK
SG7912CP
SG7912CR
SG7912CT
SG7915ACK
SG7915ACP
SG7915ACR
SG7915ACT
SG7915CK
SG7915CP
SG7915CR
SG7915CT
SG7918CK
SG7918CP
MC7805CT
MC78M05CG
MC7805K
MC7805K
MC7805K
MC7806ACK
MC7806ACT
MC7806ACT
MC7806ACT
MC7806AK
MC7806AK
MC7806AK
MC7805CK
MC7806CT
MC7806CT
MC78M06CG
MC7806K
MC7806K
MC7806K
MC7808ACK
MC7808ACT
MC78M08ACT
MC7808ACT
MC7808AK
MC7808AK
MC7808AK
MC7808CK
MC7808CT
MC7808CT
MC7808CG
MC7808K
MC7808K
MC7808K
MC7812ACK
MC7812ACT
MC7812ACT
MC7812ACT
MC7812AK
MC7812AK
MC7812AK
MC7812CK
MC7812CT
MC7812CT
MC78M12CG
MC7812K
MC7815ACK
MC7815ACT
MC7815ACT
MC7815ACT
MC7815AK
MC7815AK
MC7815AK
MC7815CK
MC7815CT
MC7815CT
MC78M15CG
MC7815K
MC7815K
MC7815K
MC7818ACK
379
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
MC7818ACT
MC7818ACT
MC7818ACT
MC7818AK
MC7818AK
MC7818AK
MC7818CK
MC7818CT
MC7818CT
MC7818CG
MC7818K
MC7818K
MC7818K
MC7824ACK
MC7824ACT
MC7824ACT
MC7824ACT
MC7824AK
MC7824AK
MC7824AK
MC7824CK
MC7824CT
MC7824CT
MC78M24CG
MC7824K
MC7824K
MC7824K
MC7905ACK
MC7905ACT
MC7905ACT
MC7905ACT
MC7905CK
MC7905CT
MC7905CT
MC7905CT
MC7905.2CK
MC7905.2CT
MC7905.2CT
MC7905.2CT
MC7908CK
MC7908CT
MC7908CT
MC7908CT
MC7912ACK
MC7912ACT
MC7912ACT
MC7912ACT
MC7912CK
MC7912CT
MC7912CT
MC7912CT
MC7915ACK
MC7915ACT
MC7915ACT
MC7915ACT
MC7915CK
MC7915CT
MC7915CT
MC7915CT
MC7918CK
MC7918CT
REFERENCE
NUMBER
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
REFERENCE
NUMBER
MOTOROLA
DIRECT
REPLACEMENT
MOTOROLA
FUNCTIONAL
EQUIVALENT
..
T.I.
1lA723CJ
1lA723CL
1lA723CN
..,.723MJ
..,.723ML
..,.A7805CKC
1lA7806CKC
..,.A7808CKC
1lA7812CKC
..,.A7815CKC
..,.A7818CKC
..,.A7824CKC
1lA78L05ACJG
1lA78L05ACLP
..,.A78L05CJG
1lA78L05CLP
1lA78L08ACJG
1lA78L08ACLP
1lA78L08CJG
1lA78L08CLP
1lA78L12ACJG
1lA78L12ACLP
..,.A78L12CJG
..,.A78L12CLP
..,.A78L15ACJG
..,.A78L 15ACLP
..,.A78L15CJG
..,.A78L15CLP
..,.A78M05CKC
1lA78M05CKD
..,.A78M05CLA
..,.A78MOSCKC
1lA78MOSCKD
1lA78MOSCLA
1lA78M08CKC
1lA78M08CKD
1lA78M08CLA
1lA78M12CKC
1lA78M12CKD
1lA78M12CLA
..,.A78M15CKC
1lA7815CKD
..,.A78M15CLA
MC1723CL
MC1723CG
MC1723CP
MC1723L
MC1723G
MC7805CT
MC7806CT
MC7808CT
MC7812CT
MC1715CT
MC7818CT
MC7824CT
MC78L05ACG
MC78L05ACP
MC78L05CG
MC78L05CP
MC78L08ACG
MC78L08ACP
MC78L08CG
MC78L08CP
MC78L12ACG
MC78L12ACP
MC78L12CG
MC78L12CP
MC78L15ACG
MC78L15ACP
MC78L15CG
MC78L15CP
MC78M05CT
MC78M05CT
MC78M05CG
MC78M06CT
MC78M06CT
MC78MOSCG
MC78MOSCT
MC78M08CT
MC78M08CG
MC78M12CT
MC7812CT
MC78M12CG
MC78M15CT
MC78M15CT
MC78M15CG
1lA78M2OCKC
IlA78M2OCKD
1lA78M2OCLA
..,.A78M24CKC
1lA78M24CKD
1lA78M24CLA
..,.A7905CKC
1lA7905.2CKC
..,.A790SCKC
1lA7908CKC
1lA7912CKC
1lA7915CKC
1lA7918CKC
1lA7924CKC
IlA79M05CKC
1lA79M06CKC
1lA79M08CKC
1lA79M12CKC
..,.A79M15CKC
1lA79M24CKC
LM109LA
LM117LA
LM209LA
LM217KC
LM217KD
LM217LA
LM309LA
LM317KC
LM317KD
LM317LA
LM340KC-5
LM340KC-6
LM340KC-8
LM340KC-12
LM340KC-15
LM340KC-18
LM340KC-24
TL494CJ
TL494CN
TL494MJ
TL495CJ
TL495CN
TL495MJ
TL7805ACKC
380
MC78M20CT
MC78M20CT
MC78M2OCG
MC78M24CT
MC78M24CT
MC78M24CG
MC7905CT
MC7905.2CT
MC7906CT
MC7908CT
MC7912CT
MC7915CT
MC7918CT
MC7924CT
MC7905CT
MC7806CT
MC7908CT
MC7912CT
MC7915CT
MC7924CT
LM109H
LM117H
LM209H
LM217K
LM217H
LM217H
LM309H
LM317T
LM317T
LM317H
LM340K-5.0
LM340K-S.O
LM340K-8.0
LM340K-12
LM340K-15
LM340K-18
LM340K-24
TL494CJ
TL494CN
TL494MJ
TL495CJ
TL495CN
TL495MJ
MC7805ACT
APPENDIX A
SWITCHMODE POWER TRANSISTOR
APPLICATION SELECTOR GUIDE
For line-operated SWITCHMODE power supplies (20 to 50 kHz, 40 to 3200
watts), this guide offers the power supply design engineer an easy way to identify
those Motorola SWITCHMODE Transistors most ideally-suited for his particular
application. To use the five tables in this guide, the designer must first:
1. Determine which of five circuits he will be using (i.e., full-bridge, halfbridge, push-pull, forward or ftyback).
2. Determine which of three line voltages he will be using (i.e., 120, 220,
or 380 Vac).
3. Determine the output power capability needed by his design (the table
covers the area of 40 to 3200 watts).
Tables 1 through 3 list devices by VCEO (sus) for use in bridge circuits at either
120, 220 or 380 volts. Tables 4 and 5 list the same devices by VCEV for use in
the push-pull, forward and ftyback circuits at either 120 or 220 volts. Within each
table, the devices are grouped by the output power capability of that circuit, and
the equivalent operating current level is also noted.
381
TABLE 1
CIRCUIT: HALF AND FULL* BRIDGE
LINE VOLTAGE: 120 VRMS
DEVICE VCEO RATING ;;.200 V
Clrcun Rating
Output
Pow....
Metal-To-204**, TO-86
Plastic-To-Z20AB, TO·126
Darlington-To-204**
Rated
IC(OP~
Device
(Watts)
(Amps
Type
YCEO
(Yolts)
40
1
2N6233
2N6421PNP
2N6078
2N3584
2N6077
2N6234
2N3585
2N6212PNP
2N6422PNP
MJ4360
2N6235
2N6213PNP
MJ4361
225
250
250
250
275
275
300
300
300
300
325
350
400
MJE13002
300
80
2
2N5838
2N5839
250
275
MJE13004
300
120
3
2N6306
MJ6502PNP
2N6307
2N6542
MJ4380
MJ4400
2N6308
MJ4381
MJ4401
250
250
300
300
300
300
350
400
400
2N6497
250
2N6498
2N6499
300
350
Device Type
RatedYCEO
RatedYCEO
(Yolts)
Device Type
(Yons)
MJ10006
350
MJ10004
350
20
MJ10015
MJ10022
400
350
30
MJ10020
MJ10021
200
250
200
5
2N6544
MJ13014
MJ6502PNP
300
350
250
MJE13006
MJE5850PNP
MJE5851PNP
300
300
350
320
400
8
10
MJ13014
2N6249
MJ13330
MJ13331
2N6250
2N6546
2N6251
MJ13332
350
200
200
250
275
300
350
350
MJE13008
300
800
1200
"NOTE: Power output ratings are for half-bridge circuit configurations, multiply by 2 for full-bridge.
*'Formerly TO-3
382
TABLE 2
Clrcun RatIng
Output
Power*
(Watts)
~OP~
(Amps
CIRCUIT: HALF AND FULL· BRIDGE
LINE VOLTAGE: 220 VRMS
DEVICE VCEO RATING ;;.400V
Darlington-T0-204··
Metal-T0-204", T~ Plastle>-TO-220AB, To-l26
Rated
Device
Rated VCEO
Rated VCEO
VCEO
(Vons)
Device Type
(Volts)
(Vons)
Device Type
Type
80
1
MJ4361
400
MJE13003
400
160
2
MJ4381
400
MJE13005
400
240
3
2N6543
MJ4401
400
400
400
5
2N6545
MJ6503PNP
MJ13015
400
400
400
MJE13007
MJE5852PNP
400
400
MJ1OO07
400
MJE13009
400
MJ10013
550
MJ10005
MJ10008
MJ10009
MJ10013
MJ10014
400
450
500
550
600
MJ1oo23
MJ10015
MJ10016
400
400
500
640
8
MJ13333
400
800
10
2N6547
MJ13333
MJ13334
MJ13335
40
400
450
500
1600
20
*NOTE: Power output ratings are for half-bridge circuit configurations, multiply by 2 for full-bridge.
**Formerly T0-3
TABLE 3
Clrcun Rating
Output
Power"
IC(OP~
(Watts)
(Amps
240
2
360
3
480
4
600
5
1200
10
CIRCUIT: HALF AND FULL· BRIDGE
LINE VOLTAGE: 380 VRMS
DEVICE VCEO RATING ;;.600V
MetaI-T0-204··, T~ Plastle>-TO-220AB, TO-126
Darlington-TO-204··
Rated
Device
Rated VCEO
Rated VCEO
VCEO
(Volts)
Type
(Vons)
Device Type
Device Type
(Volts)
MJ8500
700
MJ12oo2
750
MJE12oo7
750
MJ8501
800
700
MJ8502
MJ12003
750
MJ8503
800
MJ1oo11
750
700
MJ12004
MJ8504
MJ12oo5
MJ8505
700
750
800
MJ1oo14
*NOTE: Power output ratings are for half-bridge circuit configurations, multiply by 2 for full-bridge.
""Formerly TO-3
383
600
TABLE 4
CIRCUIT: FORWARD, PUSH-PULL" AND FLYBACK"
LINE VOLTAGE: 120 VRMS
DEVICE VCEV RATING ;;;.450 V
Circuit Rating
Metal-T()"204"-, TO-66
Output
(Watts)
(Amps
IC(OP~
Device
Type
Rated
VCEV
(VoltS)
40
1
2N3585
2N6422PNP
2N6423PNP
2N4240
450
450
450
450
80
2
120
3
2N6306
2N6307
2N6542
2N6308
2N6543
200
5
MJ6503PNP
2N6544
2N6545
320
8
400
10
800
20
Power
MJ13332
MJ13333
MJ13334
MJ13335
2N6546
Plastic-TO-220AB, TO-l26
Device Type
IRsted VCEV
Rated VCEV
Volts
(Volts)
Device Type
MJE13002
MJE13003
600
700
MJE13004
MJE13005
600
700
500
600
650
700
850
2N6499
450
450
650
850
MJE5852PNP
MJE5740
MJE13006
MJE5741
MJE13007
MJE5742
450
600
600
700
700
800
MJE13008
MJE13009
600
700
450
500
550
600
650
Dsrllngton-TO-,204--
MJ10005
MJ10007
MJ10012
450
500
550
MJ10004
MJ10005
MJ10008
MJ10009
MJ1000B
MJ10014
450
500
650
750
650
700
MJ10009
MJ10015
MJ10016
750
600
750
-NOTE: Power output ratings are for forward converter configurations (one transistor). Multiply by 2 for push-pull
circuits and divide by 2 for flyback configurations.
-'Formerly TO-3
384
TABLES
CIRCUIT: FORWARD, PUSH·PULL* AND FLYBACK*
LINE VOLTAGE: 220 VRMS
DEVICE VCEV RATING ;;;,850 V
Circuit Rating
MetaI-TO·204**, TO-66
Output
Power"
(Watts)
(Amps
IC(OP~
Device
Type
Rated
VCEV
(Vons)
160
2
MJ8500
MJ8501
MJ12002
1200
1400
1500
240
3
2N6543
MJ8502
MJ8503
MJ12003
850
1200
1400
1500
320
4
MJ12004
1500
400
5
2N6545
MJ8504
MJ8505
MJ12005
850
1200
1400
1500
560
7
MJ12010
950
800
10
2N6547
850
Plaatlo-TO·220AB, TO·126
Device Type
MJE12007
Darlington-TO·204**
Rated VCEV
Rated VCEV
(Volts)
Volts
Device Type
1500
MJ10011
1500
-NOTE: Power output ratings are for forward converter configurations (one transistor). Multiply by 2 for push-pull
circuits and divide by 2 for flyback configurations.
--Formerly T0-3
385
386
APPENDIXB
MOTOROLA SWITCHMODE RECTIFIERS
FOR SWITCHING POWER SUPPLIES
387
MOTOROLA SWITCHMODE INPUT RECTIFIERS
Total
Supply
Power
Standard Recovery for
Line Voltage Operation
Typical Circuit
Input
Current
Flyback (Ringing-Choke)
10
1.0 A 400 V
1.0 A
1.S A
2.0 A
MRS04
1NS404
MDA204
3.0A
3.0 A
2.0 A
2.0A
MRS04
1NS404
MDA204
3.0A
3.0A
2.0A
3.0A
MRS04
1NS404
MDA970AS
3.0 A
3.0A
4.0A
6.0A
MR7S4
1N1204,A,B,C
MR1124
MDS804
6.0 A
12 A
12 A
8.0 A
12 A
1N1204,A,B,C
MR1124
MDA1204
MR2004S
12 A
12 A
12 A
20A
2SA
MDA2S04
MDA3S04
1N1183,A
2S A
3SA
40A
Output
Rectifier
sow
7SW
Basic Forward Converter
Output
Output
Rectifier"
un~ ?"I I:
+IInput ~
Input
Rectifier
100W
/
Filter
Power
Inverter
II~~C Output
~I
Control
Circuitry
Basic Half-Bridge Configuration
2S0W
Output
Filter
=
t
Output r- - - ,
RectifierL _ _ _
J
"---""-J,+-t+-1-fi. :;.- -1
I
Power I
Input
Inverter 1
I
Rectifier '--~--t-::._J
I
1000 W
Line,
~~---j----'+t--_'-----1r
I -_ _---Jlnput~
T ~: :I
DC
Output
Control
Circuitry
2S00W
+
Full-Bridge and Push-Pull
388
VR
1N4004
MDA104A
MDA920A6
<1.0 A
10 W
Suggested Devices
Type
MOTOROLA SWITCHMODE OUTPUT RECTIFIERS
Schottky
for 5.0 V Outputs
Output
Current
Fast Recovery
for >5.0 V Outputs
Suggested Devices
Type
10
VR
1.0-2.0 A
1N5818
1N5821
MBR330M
MBR330M
1N5824
1.0 A
3.0A
3.0 A
3.0 A
5.0A
30 V
30V
30V
30V
30V
5.0-10 A
1N5827
MBR1530
1N5830
1N6095
15 A
15 A
25A
25A
30 V
30V
30V
30V
10-15 A
1N5830
MBR2535
5041
MBR3535
25A
25A
30A
35A
8.0-16 A
1N5827
MBR1530
1N5830
1N6095
MBR3035CT
Output
Current
Suggested Devices
Type
10
VR
1N4934
1.0 A
100 V
0.5-1.5 A
1N4934
MR851
MR831
MR801
1.0
1.0
3.0
3.0
30V
35 V
35 V
35 V
1.5-2.5 A
MR851
MR821
MR831
MR801
3.0A
5.0 A
3.0A
3.0A
15 A
15 A
25A
25A
30A
30 V
30V
30V
30 V
35 V
2.0-2.5 A
1N4934
MR851
MR801
1.0 A
3.0A
3.0 A
10-20 A
1N5827
MBR1530
1N5830
1N6095
MBR3035CT
15
15
25
25
30
A
A
A
A
A
30V
30 V
30 V
30 V
35 V
2.0-2.5 A
1N4934
MR851
MR801
1.0 A
3.0A
3.0A
30-50 A
1N5830
5041
1N6095
MBR3535
MBR3035CT
25 A
30A
25A
35 A
30 A
30V
35 V
30 V
35 V
35 V
2.0-8.0 A
1N4934
MR851
MR821
1N3880,A
MOA2501FR
1.0 A
3.0 A
5.0 A
6.0 A
25A
200 A
5051
MBR6035
MBR7535
1N6097
(IN PARALLEL)
60
60
75
50
A
A
A
A
35 V
35 V
35 V
30V
40A
1N3900
1N3910
MOA3501FR
20 A
30 A
35 A
60
60
75
50
A
A
A
A
35 V
35 V
35 V
30V
MR871
50 A
500 A
5051
MBR6035
MBR7535
1N6097
(IN PARALLEL)
<0.5 A
100 A
389
A
A
A
A
~
,
FURTHER INFORMATION ON SWITCHING REGULATORS
1. "100 kHz PET Switcher," R. Haver, Power Conversion International, April
1982.
2. "Switching and Linear Power Supply," Power Converter Design, Abraham
1. Pressman - Hayden Book Company, 1977.
3. "Power Darlington Load Line Considerations," R. J. Haver, Motorola
AN-786, April 1980.
4. "The Effect of Emitter-Base Avalanching on High Voltage Power Switching
Transistors," A. Pshaenich, Motorola AN-803, February 1980.
5. "A Symmetry Correcting Circuit for Use with the MC3420," H. Wurzburg,
Motorola EB-66A, January 1981.
6. "New ICs Perform Control and Ancillary Functions in High Performance
Switching Supplies," R. Suva and R. J. Haver, Motorola EB-78, August
1981.
7. "Half-Bridge Switching Power Supplies," R. Suva and R. J. Haver, Motorola
EB-86, June 1980.
8. "Flyback Switching Power Supplies," R. Suva and R. J. Haver, Motorola
EB-87, February 1981.
390
;.
MOTOROLA Semiconductor Products Inc.
po. BOX 20912 . PHOENIX, ARIZONA 85036 . A SUBSIDIARY OF MOTOROLA INC
10639-4
PRINTED IN liSA
6-82
lHPERIAL LlnlO
C06082
27 , Sao
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