1993_National_Power_ICs_Databook 1993 National Power ICs Databook

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4
DPVMTM
E2CMOSTM
ELSTARTM
Embedded System
Processor™
EPTM
E-Z-LlNKTM

FACTTM
FACT Quiet Series™
FAIRCADTM
Fairtech™
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FASTr™
FlashTM
GENIXTM
GNXTM
GTOTM
HEX3000™
HPCTM
HyBal™
13LI!>
ICMTM
IntegrallSETM
IntelisplayTM
Inter-LERICTM
Inter-RICTM
ISETM
ISE/06TM
ISE/08TM
ISE/16TM
·ISE32™
ISOPLANARTM
ISOPLANAR-ZTM
LERICTM
LMCMOSTM
M2CMOSTM
Macrobus™
Macrocomponent™
MAPLTM
MAXI-ROM I!>
Microbus™ data bus
MICRO-DACTM
p.talker™
Microtalker™
MICROWIRETM

MICROWIRE/PLUSTM
MOLETM
MPATM
MSTTM
Naked-8™
Nationall!>
National Semiconductorl!>
National Semiconductor
Corp. I!>
NAX800TM
Nitride PIUS™
Nitride Plus Oxide™
NMLTM
NOBUSTM
NSC800TM
NSCISETM
NSX-16TM
NS-XC-16TM
NTERCOMTM
NURAMTM
OPALTM
OXISSTM
P2CMOSTM
Perfect WatchTM
PLANTM
PLANARTM
PLAYERTM
Plus-2TM
Polycraft™
Power + Control™
POWERplanar™
QSTM
QUAD3000TM
QUIKLOOKTM
RATTM
RICTM
RTX16TM
SCXTM

SERIES/800TM
Series 320001!>
Simple Switcher™
SofChekTM
SONICTM.
SPIRETM
Staggered RefreshTM
STARTM
Starlink™
STARPLEXTM
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SuperATTM
Super-Block™
SuperChipTM
SuperScriptTM
SYS32™
TapePak®
TDSTM
TeleGate™
The National Anthem®
TLCTM
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TRI-CODETM
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Tropic Pele'TM
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TURBOTRANSCEIVERTM
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883B/RETSTM
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LIFE SUPPORT POLICY
NATIONAL'S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR
SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:
2. A critical component is any component of a life support
1. Life support devices or systems are devices or systems
which, (a) are intended for surgical implant into the body,
device or system whose failure to perform can be reasonably expected to cause the failure of the life support deor (b) support or sustain life, and whose failure to pervice or system, or to affect its safety or effectiveness.
form, when properly used in accordance with instructions
for use provided in the labeling, can be reasonably expected to result in a significant injury to the user.
NatlonalSemlconductorCorporatlon 2900 Semiconductor Drive, P.O. Box 58090, Santa Clara, California 95052-8090 1·800·272-9959
TWX (910) 339-9240
Nalional does not assume any responsibility for use of any circuilry described, no clrcu~ palenllicenses are Implied, and Nalional reserves the righI, 01 any time
wilhout notice, 10 change said circuitry or specHicalions.

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Product Status Definitions

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Definition of Terms

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Data Sheet Identification

Product Status

Advance Information

Formative or
In Design

This data sheet contains the design specifications for product
development. Specifications may change in any manner without notice.

Preliminary

First
Production

This data sheet contains preliminary data, and supplementary data will
be published at a later date. National Semiconductor Corporation
reserves the right to make changes at any time without notice in order
to Improve design and supply the best possible product.

Full
Production

This data sheet contains final specifications. National Semiconductor
Corporation reserves the right to make changes at any time without
notice in order to improve design and supply the best possible product.

Not In Production

This data sheet contains specifications on a product that has been
discontinued by National Semiconductor Corporation. The data sheet
is printed for reference information only.

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Definition

National Semiconductor Corporation reserves the right to make changes without fur:ther notice to any products herein to
improve reliability, function or design. National does not assume any liability arising out of the application or use of any product
or circuit described herein; neither does it convey any license under Its patent rights, nor the rights of others.

iii

Table of Contents
Alphanumeric Index. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Additional Available Linear Devices . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Cross Reference by Part Number. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Industry Package Cross Reference Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Section 1 Linear Voltage Regulators
Linear Voltage Regulators Definition ofTerms . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Linear Voltage Regulators Selection Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
* LH0075 Positive Precision Programmable Regulator
* LH0076 Negative Precision Programmable Regulator
* LH7001 PositivelNegative Adjustable Regulator
LM104/LM204/LM304 Negative Regulators.....................................
LM1 05/LM205/LM305lLM305A/LM376 Voltage Regulators. . . . . . . . . . . . . . . . . . .. . . .
LM1 09/LM309 5-Volt Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM117/LM117A1LM317/LM317A 3-Terminal Adjustable Regulators. ....... ... .....
LM117HVILM317HV 3-Terminal Adjustable Regulators ...........................
.LM120/LM320 Series 3-Terminal Negative Regulators. . . . .. .. . .... .... ...... .....
LM123A1LM123/LM323A1LM323 3-Amp, 5-Volt Positive Regulators. . . . . . . . . . . . . . . .
LM125/LM325/LM325A, LM126/LM326 Voltage Regulators. . . . . . . . . . . . . . . . . . . . . . .
LM133/LM333 3-Amp Adjustable Negative Voltage Regulators. . .... ....... ... ... ..
LM137/LM337 3-Terminal Adjustable Negative Regulators........................
LM137HV/LM337HV 3-Terminal Adjustable Negative Regulators (High Voltage)......
LM138/LM338 5-Amp Adjustable Regulators....................................
LM140AlLM140/LM340AlLM340/LM7800/LM7800C Series 3-Terminal Positive
Regulators................................................................
LM140L/LM340L Series 3-Terminal Positive Regulators. .. ... ... ....... .. .. .. .....
LM145/LM345 Negative 3-Amp Regulators ............................... ~. .....
LM150/LM350/LM350A 3-Amp Adjustable Power Regulators ................ ~ . . . . .
LM196/LM396 1O-Amp Adjustable Voltage Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM317L 3-Terminal Adjustable Regulator. .. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM320L, LM79LXXAC Series 3-Terminal Negative Regulators......................
LM337L 3-Terminal Adjustable Regulator........................................
LM341/LM78MXX Series 3-Terminal Positive Regulators..........................
LM342 Series 3-Terminal Positive Regulator.....................................
LM431 A Adjustable Precision Zener Shunt Regulator .............................
LM723/LM723C Voltage Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM78G 4-Terminal Adjustable Regulator.........................................
LM78LXX Series 3-Terminal Positive Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM78MG 4-Terminal Adjustable Voltage Regulator. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM79MXX Terminal Negative Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM79XX Series 3-Terminal Negative Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Section 2 Low Dropout Voltage Regulators
Low Dropout Voltage Regulators-Definition ofTerms. . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Low Dropout Regulators-Selection Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM330 3-Terminal Positive Regulator.... .. .. .. .. ... ... ... .. . .. . . . .. . . . ... . .....
LM2925 Low Dropout Regulator with Delayed Reset . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM2926/LM2927 Low Dropout Regulators with Delayed Reset. . . . . . . . . . . . . . . . .. . . .
LM2930 3-Terminal Positive Regulator....... . ..... ... .. ... ... ... ... .. ..... .... .
LM2931 Series Low Dropout Regulators. ...... ..... .. ... ... .. . ... ... .. ... .. .... .
LM2935 Low Dropout Dual Regulator ...........................................
LM2936 Ultra-Low Quiescent Current 5V Regulator . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM2937 500 mA Low Dropout Regulator. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
'See Appendix G

iv

vii
x
xxiv
xxxvi
1-3
1-4

1-8
1-12
1-19
1-25
1-37
1-47
1-56
1-62
1-70
1-77
1-83
1-89
1-101
1-112
1-116
1-120
1-132
1-144
1-155
1-159
1-161
1-170
1-175
1-182
1-191
1-197
1-207
1-213
1-220
2-3
2-4
2-6
2-10
2-16
2-24
2-29
2-36
2-44
2-49

Table of Contents (Continued)
Section 2 Low Dropout Voltage Regulators (Continued)
LM2940/LM2940C 1A Low Dropout Regulators ... . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM2941 ILM2941 C 1A Low Dropout Adjustable Regulators ........................
LM2984 Microprocessor Power Supply System. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM2990 Negative Low Oropout Regulator .......................................
LM2991 Negative Low Oropout Adjustable Regulator. . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LP2950/LP2950AC/LP2950C 5V and LP2951 ILP2951 AC/LP2951 C Adjustable
Micropower Voltage Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LP2952/LP2952A/LP2953/LP2953A Adjustable Micropower Low-Dropout Voltage
Regulators ................................................................
LP2954/LP2954A 5V Micropower Low-Dropout Voltage Regulators. . . . . . . . .. . . . . .. .
Section 3 Switching Voltage Regulators
Switching Voltage Regulators Definition of Terms. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Switching Voltage Regulators Selection Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
HS7067 7-Amp, Multimode, High Efficiency Switching Regulator. .. . . . . .. . . . . . . . . . . .
LH1605/LH1605C 5 Amp, High Efficiency Switching Regulators. . . . . . . . . . . . . . . . . . . .
LM1524D/LM25240/LM3524D Regulating Pulse Width Modulators. . . . . . . . . . . . . . . . .
LM2574/LM2574HV Series Simple Switcher 0.5A Step-Oown Voltage Regulators ....
LM1575/LM1575HVILM2575/LM2575HV Simple Switcher 1A Step-Down Voltage
Regulators ................................................................
LM2576/LM2576HV Simple Switcher 3A Step-Down Voltage Regulators. . . . . . . . . . . .
LM1577 ILM2577 Simple Switcher Step-Up Voltage Regulators. . . . . . . . . . . . . . . . . . . . .
LM1578A/LM2578A/LM3578A Switching Regulators.............................
LM78S40 Universal Switching Regulator Subsystem ..............................
LMC7660 Switched Capacitor Voltage Converter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Section 4 Motion Control
Motion Control and Motor Drive Selection Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM12L 80W Operational Amplifier..............................................
LM621 Brushless Motor Commutator. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM628/LM629 Precision Motion Controllers. . . . . . . . . . . . . . .. . . . .. . . . . . . . .. . . . . ...
LM 18293 Four Channel Push-Pull Driver. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .. . . . . . . .
LM18298 Dual Full-Bridge Driver...............................................
LMD18200 3A, 55VH-Bridge . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LMD18201 3A, 55VH-Bridge ...................................................
Section 5 Peripheral Drivers
Peripheral Drivers-Introduction. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Peripheral Drivers-Selection Guide ............................................
DP731 0/DP831 0/DP7311 IDP8311 Octal Latched Peripheral Drivers. . . . . . . . . . . . . . .
DS1631 IDS3631 IDS1632/DS3632/DS1633/DS3633/0S1634/DS3634 CMOS Dual
Peripheral Drivers .......................................... . . . . . . . . . . . . . . . .
DS2001 IDS9665/DS2002/DS9666/DS2003/DS9667 IDS2004/DS9668 High.
Current/Voltage Darlington Drivers. . . . . . . . . . . . . . . . . .. . . . . . . .. . . . . . . . . . . . . . . . .
DS3654 Printer Solenoid Driver. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
DS3658 Quad High Current Peripheral Driver. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
DS3668 Quad Fault Protected Peripheral Driver . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
DS3669 Quad High Current Peripheral Driver. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
DS3680 Quad Negative Voltage Relay Driver. . . . . . . . . .. . . . ... . . . . . . . . . . . . . . . . . .. .
DS55451 12/3/4, DS75450/1 12/314 Series Dual Peripheral Drivers. . . . . . . . . . . . . . . . .
Section 6 High Current Switches
High Current Switch Selection Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM1921 1 Amp Industrial Switch. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
"'See Appendix G

v

2-54
2-63
2-69
2-82
2-89
2-95
2-108
2-121
3-3
3-5
3-7
3-16
3-19
3-36
3-54
3-71
3-87
3-109
3-123
3-130
4-3
4-4
4-17
4-28
4-49
4-55
4-61
4-70
5-3
5-4
5-5
5-12
5-17
5-22
5-26
5-29
5-32
5-35
5-38
6-3
6-4

Table of Contents (Continued)
Section 6 High Current Switches (Continued)
LM1950 750 mA High Side Switch.. . .. . .. .. . . . .... ... . .. .... ....... . . . ... .. ... .
LM1951 Solid State 1 Amp Switch..............................................
LMD18400 Quad High Side Driver. .. ... .. .. . .. ... . .... .... .. ... .. ... .. . .... . . ..
Section 7 Surface Mount
Surface Mount. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
AN-450 Small Outline (SO) Package Surface Mounting Methods-Parameters and
Their Effect on Product Reliability. . . . . . . . . . . . . . • . . . .. . . . . . . . . . . . . . . . . . . . . . . . . .
Section 8 Appendices/Physical Dimensions
Appendix A General Product Marking and Code Explanation •..........•...........
Appendix B Devicel Application Literature Cross-Reference . . . . . . . . . . . . . . . . . . . . . . . .
Appendix C Summary of Commercial Reliability Programs. . . . . . . . . . . . . . . . . . . . . . . . . .
Appendix D Military Aerospace Programs from National Semiconductor. . . . . . . . . . . . . .
Appendix E Understanding Integrated Circuit Package Power Capabilities. . • . . . . . • • . .
Appendix F How to Get the Right Information from a Datasheet . . . . . . . . . . . . . . . . . . . . .
Appendix G Obsolete Product Replacement Guide... . .•. •.. .... .•. .. . ... ..... ... .
Appendix H Safe Operating Areas for Peripheral Drivers . . . . . . . • . . . . . . . . . . . . . . . . . . .
Physical Dimensions. • . . . . . . • . . . . • . . . • . . . . . . . . . . • . . . . . . . . . . . . . . . . . . . . . . • . . . . . .
Bookshelf
Distributors

·s•• Appendix G
vi

6-9
6-14
6-22
7-3
7-23
8-3
8-4
8-11
8-13
8-22
8-27
8-31
8-33
8-41

Alpha-Numeric Index
AN-450 Small Outline (SO) Package Surface Mounting Methods-Parameters and Their
Effect on Product Reliability .............................................................. 7-23
DP731 0 Octal Latched Peripheral Driver ...................................................... 5-5
DP7311 Octal Latched Peripheral Driver ...................................................... 5-5
DP8310 Octal Latched Peripheral Driver ...................................................... 5-5
DP8311 Octal Latched Peripheral Driver ...................................................... 5-5
DS1631 CMOS Dual Peripheral Driver ....................................................... 5-12
DS1632 CMOS Dual Peripheral Driver ....................................................... 5-12
D81633 CMOS Dual Peripheral Driver ....................................................... 5-12
DS1634 CMOS Dual Peripheral Driver ....................................................... 5-12
DS2001 High CurrentlVoltage Darlington Driver .............................................. 5-17
DS2002 High CurrentlVoltage Darlington Driver .............................................. 5-17
DS2003 High CurrentlVoltage Darlington Driver .............................................. 5-17
DS2004 High CurrentlVoltage Darlington Driver .............................................. 5-17
DS3631 CMOS Dual Peripheral Driver ....................................................... 5-12
DS3632 CMOS Dual Peripheral Driver ....................................................... 5-12
DS3633 CMOS Dual Peripheral Driver ....................................................... 5-12
DS3634 CMOS Dual Peripheral Driver ....................................................... 5-12
DS3654 Printer Solenoid Driver ...................................................•......... 5-22
DS3658 Quad High Current Peripheral Driver ................................................. 5-26
DS3668 Quad Fault Protected Peripheral Driver .............................................. 5-29
DS3669 Quad High Current Peripheral Driver ................................................. 5-32
DS3680 Quad Negative Voltage Relay Driver ................................................. 5-35
DS9665 High CurrentlVoltage Darlington Driver .............................................. 5-17
DS9666 High CurrentlVoltage Darlington Driver .............................................. 5-17
DS9667 High CurrentlVoltage Darlington Driver .............................................. 5-17
DS9668 High CurrentlVoltage Darlington Driver .............................................. 5-17
DS55451 Series Dual Peripheral Drivers ..................................................... 5-38
DS55452 Series Dual Peripheral Drivers ..................................................... 5-38
DS55453 Series Dual Peripheral Drivers ..................................................... 5-38
DS55454 Series Dual Peripheral Drivers ..................................................... 5-38
DS75450 Series Dual Peripheral Drivers ..................................................... 5-38
DS75451 Series Dual Peripheral Drivers ..................................................... 5-38
DS75452 Series Dual Peripheral Drivers ..................................................... 5-38
DS75453 Series Dual Peripheral Drivers ..................................................... 5-38
DS75454 Series Dual Peripheral Drivers ..................................................... 5-38
HS7067 7-Amp, Multimode, High Efficiency Switching Regulator ................................. 3-7
* LH0075 Positive Precision Programmable Regulator
* LH0076 Negative Precision Programmable Regulator
LH 1605 5 Amp, High Efficiency Switching Regulator .......................................... 3-16
* LH7001 Positive/Negative Adjustable Regulator
LM 12L 80W Operational Amplifier ........................................................... 4-4
LM78G 4-Terminal Adjustable Regulator ................................................... 1-191
LM78LXX Series 3-Terminal Positive Regulators ............................................. 1-197
LM78MG 4-Terminal Adjustable Voltage Regulator .......................................... 1-207
LM78MXX Series 3-Terminal Positive Regulator ............................................. 1-161
LM78S40 Universal Switching Regulator Subsystem ......................................... 3-123
LM79LXXAC Series 3-Terminal Negative Regulator .......................................... 1-155
LM79MXX Terminal Negative Regulators ................................................... 1-213
LM79XX Series 3-Terminal Negative Regulators ............................................. 1-220
LM104 Negative Regulator .................................................................. 1-8
*See Appendix G

vii

Alpha-Numeric Index (Continued)
LM105 Voltage Regulator ................................................................. 1-12
LM109 5-Volt Regulator ................................................................... 1-19
LM117 3-Terminal Adjustable Regulator ..................................................... 1-25
LM 117HV 3-Terminal Adjustable Regulator .................................................. 1-37
LM120 Series 3-Terminal Negative Regulator ................................................ 1-47
LM123 3-Amp, 5-Volt Positive Regulator ..................................................... 1-56
LM125 Voltage Regulator ................................................................. 1-62
LM126 Voltage Regulator ................................................................. 1-62
LM133 3-Amp Adjustable Negative Voltage Regulator ......................................... 1-70
LM137 3-Terminal Adjustable Negative Regulator ............................................ 1-77
LM137HV 3-Terminal Adjustable Negative Regulator (High Voltage) ............................. 1-83
LM 138 5-Amp Adjustable Regulator ......................................................... 1-89
LM140 Series 3-Terminal Positive Regulator ................................................ 1-101
LM140L Series 3-Terminal Positive Regulator ............................................... 1-112
LM145 Negative 3-Amp Regulator ......................................................... 1-116
LM150 3-Amp Adjustable Power Regulator ................................................. 1-120
LM196 10-Amp Adjustable Voltage Regulator ............................................... 1-132
LM204 Negative Regulator .................................................................. 1-8
LM205 Voltage Regulator ................................................................. 1-12
LM304 Negative Regulator .................................................................. 1-8
LM305 Voltage Regulator ................................................................. 1-12
LM309 5-Volt Regulator ................................................................... 1-19
LM317 3-Terminal Adjustable Regulator ..................................................... 1-25
LM317HV 3-Terminal Adjustable Regulator .................................................. 1-37
LM317L 3-Terminal Adjustable Regulator ................................................... 1-144
LM320 Series 3-Terminal Negative Regulator ................................................ 1-47
LM320L Series 3-Terminal Negative Regulator .............................................. 1-155
LM323 3-Amp, 5-Volt Positive Regulator ..................................................... 1-56
LM325 Voltage Regulator ................................................................. 1-62
LM326 Voltage Regulator ................................................................. 1-62
LM330 3-Terminal Positive Regulator ........................................................ 2-6
LM333 3-Amp Adjustable Negative Voltage Regulator ......................................... 1-70
LM337 3-Terminal Adjustable Negative Regulator ............................................ 1-77
LM337HV 3-Terminal Adjustable Negative Regulator (High Voltage) ............................. 1-83
LM337L 3-Terminal Adjustable Regulator ................................................... 1-159
LM338 5-Amp Adjustable Regulator ......................................................... 1-89
LM340 Series 3-Terminal Positive Regulator ................................................ 1-101
LM340L Series 3-Terminal Positive Regulator ............................................... 1-112
LM341 Series 3-Terminal Positive Regulator ................................................ 1-161
LM342 Series 3-Terminal Positive Regulator ................................................ 1-170
LM345 Negative 3-Amp Regulator ......................................................... 1-116
LM350 3-Amp Adjustable Power Regulator ................................................. 1-120
LM376 Voltage Regulator ................................................................. 1-12
LM39610-Amp Adjustable Voltage Regulator ............................................... 1-132
LM431A Adjustable Precision Zener Shunt Regulator ........................................ 1-175
LM621 Brushless Motor Commutator ....................................................... 4-17
LM628 Precision Motion Controller ......................................................... 4-28
LM629 Precision Motion Controller ......................................................... 4-28
LM723 Voltage Regulator ................................................................ 1-182
LM1524D Regulating Pulse Width Modulator ................................................. 3-19
LM1575 Simple Switcher 1A Step-Down Voltage Regulator .................................... 3-54
'See Appendix G

viii

Alpha-Numeric

Index(continUed)

LM1575HV Simple Switcher 1A Step-Down Voltage Regulator ................................. 3-54
LM1577 Simple Switcher Step-Up Voltage Regulator .......................................... 3-87
LM1578A Switching Regulator ............................................................ 3-109
LM1921 1 Amp Industrial Switch ............................................................. 6-4
LM1950 750 rnA High Side Switch ........................................................... 6-9
LM1951 Solid State 1 Amp Switch .......................................................... 6-14
LM2524D Regulating Pulse Width Modulator ................................................. 3-19
LM2574 Simple Switcher 0.5A Step-Down Voltage Regulator ................................... 3-36
LM2574HV Simple Switcher 0.5A Step-Down Voltage Regulator ................................ 3-36
LM2575 Simple Switcher 1A Step-Down Voltage Regulator .................................... 3-54
LM2575HV Simple Switcher 1A Step-Down Voltage Regulator ................................. 3-54
LM2576 Simple Switcher 3A Step-Down Voltage Regulator .................................... 3-71
LM2576HV Simple Switcher 3A Step-Down Voltage Regulator ................................. 3-71
LM2577 Simple Switcher Step-Up Voltage Regulator .......................................... 3-87
LM2578A Switching Regulator .................................................•.......... 3-109
LM2925 Low Dropout Regulator with Delayed Reset .......................................... 2-10
LM2926 Low Dropout Regulator with Delayed Reset .......................................... 2-16
LM2927 Low Dropout Regulator with Delayed Reset .......................................... 2-16
LM2930 3-Terminal Positive Regulator ...................................................... 2-24
LM2931 Series Low Dropout Regulators ..................................................... 2-29
LM2935 Low Dropout Dual' Regulator ....................................................... 2-36
LM2936 Ultra-Low Quiescent Current 5V Regulator ........................................... 2-44
LM2937 500 rnA Low Dropout Regulator .................................................... 2-49
LM2940/LM2940C 1A Low Dropout Regulators .............................................. 2-54
LM2941 ILM2941 C 1A Low Dropout Adjustable Regulators .................................... 2-63
LM2984 Microprocessor Power Supply System ............................................... 2-69
LM2990 Negative Low Dropout Regulator ................................................... 2-82
LM2991 Negative Low Dropout Adjustable Regulator .......................................... 2-89
LM3524D Regulating Pulse Width Modulator ................................................. 3-19
LM3578A Switching Regulator ............................................................ 3-109
LM7800 Series 3-Terminal Positive Regulator ............................................... 1-101
LM18293 Four Channel Push-Pull Driver ..................................................... 4-49
LM18298 Dual Full-Bridge Driver ........................................................... 4-55
LMC7660 Switched Capacitor Voltage Converter ............................................ 3-130
LMD18200 3A, 55VH-Bridge ............................................................... 4-61
LMD18201 3A,55VH-Bridge ............................................................... 4-70
LMD18400 Quad High Side Driver .......................................................... 6-22
LP2950 5V Adjustable Micropower Voltage Regulator ......................................... 2-95
LP2951 Adjustable Micropower Voltage Regulator ............................................ 2-95
LP2952 Adjustable Micropower Low-Dropout Voltage Regulator ............................... 2-108
LP2953 Adjustable Micropower Low-Dropout Voltage Regulator ............................... 2-108
LP2954 5V Micropower Low-Dropout Voltage Regulator ...................................... 2-121

'See Appendix G

ix

Additional Available linear Devices
54ACT715 Programmable Video Sync Generator ........................ Section 3
74ACT715 Programmable Video Sync Generator ........................ Section 3
ADC0800 8-Bit AID Converter ........................................ Section 2
ADC0801 8-Bit p.P Compatible AID Converter .......................... Section 2
ADC0802 8-Bit p.P Compatible AID Converter .......................... Section 2
ADC0803 8-Bit p.P Compatible AID Converter .......................... Section 2
ADC0804 8-Bit p.P Compatible AID Converter .......................... Section 2
ADC0805 8-Bit p.P Compatible AID Converter .......................... Section 2
ADC0808 8-Bit p.P Compatible AID Converter with 8-Channel Multiplexer .. Section 2
ADC0809 8-Bit p.P Compatible AID Converter with 8-Channel Multiplexer .. Section 2
ADC0811 8-Bit Serial 1/0 AID Converter with 11-Channel Multiplexer ...... Section 2
ADC0816 8-Bit p.P Compatible AID Converter with 16-Channel
Multiplexer ....................................................... Section 2
ADC0817 8-Bit p.P Compatible AI D Converter with 16-Channel
Multiplexer ....................................................... Section 2
ADC0819 8-Bit Serial 1/0 AID Converter with 19-Channel Multiplexer ...... Section 2
ADC0820 8-Bit High Speed p.P Compatible AID Converter with
TracklHold Function .............................................. Section 2
ADC0831 8-Bit Serial 1/0 AID Converter with Multiplexer Options ......... Section 2
ADC0832 8-Bit Serial 1/0 AID Converter with Multiplexer Options ......... Section 2
ADC0833 8-Bit Serial 1/0 AID Converter with 4-Channel Multiplexer ....... Section 2
ADC0834 8-Bit Serial 1/0 AID Converter with Multiplexer Options ......... Section 2
ADC0838 8-Bit Serial 1/0 AID Converter with Multiplexer Options ......... Section 2
ADC0841 8-Bit p.P Compatible AID Converter .......................... Section 2
ADC0844 8-Bit p.P Compatible AID Converter with Multiplexer Options ..... Section 2
ADC0848 8-Bit p.P Compatible AID Converter with Multiplexer Options ..... Section 2
ADC0851 8-Bit Analog Data Acquisition and Monitoring System ........... Section 1
ADC0852 Multiplexed Comparator with 8-Bit Reference Divider ........... Section 2
ADC0854 Multiplexed Comparator with 8-Bit Reference Divider ........... Section 2
ADC0858 8-Bit Analog Data Acquisition and Monitoring System ........... Section 1
ADC0881 8-Bit 20 MSPS Flash AID Converter .......................... Section 2
ADC0882 8-Bit 20 MSPS Flash AID Converter .......................... Section 2
ADC08031 8-Bit High-Speed Serial 1/0 AID Converter with Multiplexer
Options, Voltage Reference, and TracklHold Function ................. Section 2
ADC08032 8-Bit High-Speed Serial 1/0 A/D Converter with Multiplexer
Options, Voltage Reference, and Track/Hold Function ................. Section 2
ADC08034 8-Bit High-Speed Serial I/O A/D Converter with Multiplexer
Options, Voltage Reference, and Track/Hold Function ................. Section 2
ADC08038 8-Bit High-Speed Serial I/O AID Converter with Multiplexer
Options, Voltage Reference, and Track/Hold Function ................. Section 2
ADC08061 500 ns AID Converter with S/H Function and Input Multiplexer .. Section 2
ADC08062 500 ns AID Converter with S/H Function and Input Multiplexer .. Section 2
ADC08064 500 ns AID Converter with S/H Function and Input Multiplexer .. Section 2
ADC08068 500 ns AID Converter with S/H Function and Input Multiplexer .. Section 2
ADC08131 8-Bit High-Speed Serial I/O AID Converter with Multiplexer
Options, Voltage Reference, and TracklHold Function ................. Section 2
ADC08134 8-Bit High-Speed Serial 1/0 AID Converter with Multiplexer
Options, Voltage Reference, and TracklHold Function ................. Section 2
ADC08138 8-Bit High-Speed Serial I/O A/D Converter with Multiplexer
Options, Voltage Reference, and TracklHold Function ................. Section 2

x

App. Specific
App. Specific
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition

Additional Available Linear Devices (Continued)
ADC08161 500 ns AID Converter with S/H Function, 2.5V Bandgap
Reference, and Input Multiplexer .................................... Section 2
ADC08164 500 ns AID Converter with S/H Function, 2.5V Bandgap
Reference, and Input Multiplexer .................................... Section 2
ADC08168 500 ns A/D Converter with S/H Function, 2.5V Bandgap
Reference, and Input Multiplexer .................................... Section 2
ADC08231 8-Bit 2 f.ts Serial /10 AID Converter with MUX, Reference, and
Track/Hold ....................................................... Section 2
ADC08234 8-Bit 2 f.ts Serial If 0 AID Converter with MUX, Reference, and
Track/Hold ....................................................... Section 2
ADC08238 8-Bit 2 f.ts Serial /10 A/D Converter with MUX, Reference, and
Track/Hold ....................................................... Section 2
ADC1001 1O-Bit f.tP Compatible A/D Converter ......................... Section 2
ADC1005 10-Bit f.tP Compatible AID Converter ......................... Section 2
ADC1021 1O-Bit f.tP Compatible AID Converter ......................... Section 2
ADC1025 1O-Bit f.tP Compatible AID Converter ......................... Section 2
ADC1031 1O-Bit Serial /10 AID Converter with Analog Multiplexer and
Track/Hold Function .............................................. Section 2
ADC1034 1O-Bit Serial /10 AID Converter with Analog Multiplexer and
Track/Hold Function .............................................. Section 2
ADC1038 1O-Bit Serial /10 AID Converter with Analog Multiplexer and
Track/Hold Function .............................................. Section 2
ADC1061 1O-Bit High-Speed f.tP-Compatible AID Converter with
Track/Hold Function .............................................. Section 2
ADC1205 12-Bit Plus Sign f.tP Compatible A/D Converter ..............•. Section 2
ADC1210 12-Bit CMOS AID Converter ................................. Section 2
ADC1211 12-Bit CMOS AID Converter ................................. Section 2
ADC1225 12-Bit Plus Sign f.tP Compatible AID Converter ................ Section 2
ADC1241 Self-Calibrating 12-Bit Plus Sign f.tP-Compatible AID Converter
with Sample/Hold ................................................. Section 2
ADC1251 Self-Calibrating 12-Bit Plus Sign AID Converter with
Sample/Hold ..................................................... Section 2
ADC3511 3%-Digit Microprocessor Compatible AID Converter ........... Section 2
ADC3711 3%-Digit Microprocessor Compatible AID Converter ........... Section 2
ADC10061 1O-Bit 600 ns AID Converter with Input Multiplexer and
Sample/Hold ..................................................... Section 2
ADC10062 1O-Bit 600 ns AID Converter with Input Multiplexer and
Sample/Hold ..................................................... Section 2
ADC10064 1O-Bit 600 ns A/D Converter with Input Multiplexer and
Sample/Hold ...........•......................................... Section 2
ADC1 0154 10-Bit Plus Sign 4 f.ts ADC with 4- or 8-Channel MUX,
Track/Hold and Reference ......................................... Section 2
ADC1 0158 1O-Bit Plus Sign 4 f.ts ADC with 4- or 8-Channel MUX,
Track/Hold and Reference •........................................ Section 2
ADC10461 1O-Bit 600 ns AID Converter with Input Multiplexer and
Sample/Hold ..................................................... Section 2
ADC10462 1O-Bit 600 ns AID Converter with Input Multiplexer and
Sample/Hold ..................................................... Section 2
ADC10464 1O-Bit 600 ns A/D Converter with Input Multiplexer and
Sample/Hold ..................................................... Section 2

xi

Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition

Additional Available

linear Devices(ContinUed)

ADC10662 10-Bit 360 ns AID Converter with Input Multiplexer and
Sample/Hold ..................................................... Section 2
ADC10664 1O-Bit 360 ns AID Converter with Input Multiplexer and
Sample/Hold ..................................................... Section 2
ADC10731 1O-Bit Plus Sign Serial I/O AID Converter with MUX,
Sample/Hold and Reference ....................................... Section 2
ADC10732 10-Bit Plus Sign Serial I/O AID Converter with MUX,
Sample/Hold and Reference ....................................... Section 2
ADC10734 10-Bit Plus Sign Serial I/O AID Converter with MUX,
Sample/Hold and Reference ....................................... Section 2
ADC10738 1O-Bit Plus Sign Serial I/O AID Converter with MUX,
Sample/Hold and Reference ....................................... Section 2
ADC10831 1O-Bit Plus Sign Serial I/O A/D Converter with MUX,
Sample/Hold and Reference ....................................... Section 2
ADC10832 1O-Bit Plus Sign Serial 110 A/D Converter with MUX,
Sample/Hold and Reference ....................................... Section 2
ADC10834 10-Bit Plus Sign Serial I/O AID Converter with MUX,
Sample/Hold and Reference ....................................... Section 2
ADC10838 1O-Bit Plus Sign Serial I/O AID Converter with MUX,
Sample/ Hold and Reference ....................................... Section 2
ADC12030 Self-Calibrating 12-Bit Plus Sign Serial I/O AID Converter with
MUX and Sample/Hold ............................................ Section 2
ADC12032 Self-Calibrating 12-Bit Plus Sign Serial I/O AID Converter with
MUX and Sample/Hold ............................................ Section 2
ADC12034 Self-Calibrating 12-Bit Plus Sign Serial I/O AID Converter with
MUX and Sample/Hold ............................................ Section 2
ADC12038 Self-Calibrating 12-Bit Plus Sign Serial I/O AID Converter with
MUX and Sample/Hold ............................................ Section 2
ADC12441 Dynamically-Tested Self-Calibrating 12-Bit Plus Sign AID
Converter with Sample/ Hold .............................•......... Section 2
ADC12451 Dynamically-Tested Self-Calibrating 12-Bit Plus Sign AID
Converter with Sample/Hold ....................................... Section 2
ADD3501 3%-Digit DVM with Multiplexed 7-Segment Output. ............. Section 2
ADD3701 3%-Digit DVM with Multiplexed 7-Segment Output .............. Section 2
AF100 Universal Active Filter ......................................... Section 7
AF151 Dual Universal Active Filter ..................................... Section 7
AH0014 Dual DPST-TIL/DTL Compatible MOS Analog Switch ............ Section 8
AH0015 Quad SPST Dual DPST-TIL/DTL Compatible MOS Analog
Switch ........................................................... Section 8
AH0019 Dual DPST-TTL/DTL Compatible MOS Analog Switch ............ Section 8
AH5009 Monolithic Analog Current Switch .............................. Section 8
AH5010 Monolithic Analog Current Switch .............................. Section 8
AH5011 Monolithic Analog Current Switch .............................. Section 8
AH5012 Monolithic Analog Current Switch .............................. Section 8
AH5020C Monolithic Analog Current Switch ............................ Section 8
CD4016B Quad Bilateral Switch ....................................... Section 8
CD4051B Single 8-Channel Analog Multiplexer/Demultiplexer ............ Section 8
CD4052B Dual4-Channel Analog Multiplexer/Demultiplexer .............. Section 8
CD4053B Triple 2-Channel Analog Multiplexer/Demultiplexer ............. Section 8
CD4066B Quad Bilateral Switch ....................................... Section 8
CD4529BC Dual 4-Channel or 8-Channel Analog Data Selector ........... Section 8

xii

Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition

Additional Available Linear Devices (Continued)
DAC0800 8-Bit Df A Converter ........................................ Section 3
DAC0801 8-Bit Df A Converter ........................................ Section 3
DAC0802 8-Bit Df A Converter ........................................ Section 3
DAC0806 8-Bit Df A Converter ........................................ Section 3
DAC0807 8-Bit Df A Converter ........................................ Section 3
DAC0808 8-Bit Df A Converter ........................................ Section 3
DAC0830 8-Bit p.P Compatible Double-Buffered Df A Converter ........... Section 3
DAC0831 8-Bit p.P Compatible Double-Buffered Df A Converter ........... Section 3
DAC0832 8-Bit p.P Compatible Double-Buffered Df A Converter ........... Section 3
DAC0854 Quad 8-Bit Voltage-Output Serial Df A Converter with Readback .. Section 3
DAC0890 Dual 8-Bit p.P-Compatible Df A Converter ...................... Section 3
DAC1000 p.P Compatible, Double-Buffered Df A Converter ............... Section 3
DAC1001 p.P Compatible, Double-Buffered Df A Converter ............... Section 3
DAC1002 p.P Compatible, Double-Buffered Df A Converter ............... Section 3
DAC1 006 p.P Compatible, Double-Buffered Df A Converter ............... Section 3
DAC1007 p.P Compatible, Double-Buffered Df A Converter ............... Section 3
DAC1008 p.P Compatible, Double-Buffered Df A Converter ............... Section 3
DAC1020 10-Bit Binary Multiplying Df A Converter ....................... Section 3
DAC1021 10-Bit Binary Multiplying Df A Converter ....................... Section 3
DAC1022 10-Bit Binary Multiplying Df A Converter ....................... Section 3
DAC1208 12-Bit p.P Compatible Double-Buffered Df A Converter .......... Section 3
DAC1209 12-Bit p.P Compatible Double-Buffered Df A Converter .......... Section 3
DAC1210 12-Bit p.P Compatible Double-Buffered Df A Converter .......... Section 3
DAC1218 12-Bit Multiplying DfA Converter ............................. Section 3
DAC1219 12-Bit Multiplying DfA Converter ............................. Section 3
DAC1220 12-Bit Binary Multiplying Df A Converter ....................... Section 3
DAC1221 12-Bit Binary Multiplying Df A Converter ....................... Section 3
DAC1222 12-Bit Binary Multiplying Df A Converter ....................... Section 3
DAC1230 12-Bit p.P Compatible Double-Buffered Df A Converter .......... Section 3
DAC1231 12-Bit p.P Compatible Double-Buffered Df A Converter .......... Section 3
DAC1232 12-Bit p.P Compatible Double-Buffered Df A Converter .......... Section 3
DAC1265 Hi-Speed 12-Bit Df A Converter with Reference ................ Section 3
DAC1266 Hi-Speed 12-Bit Df A Converter .............................. Section 3
DH0006 Current Driver ............................................... Section 8
DH0006C Current Driver ............................................. Section 8
DH0008 High Voltage, High Current Driver .............................. Section 8
DH0011A High Voltage High "Current Driver ............................. Section 8
DH0034 High Speed Dual Level Translator ............................. Section 8
DH0035 PIN Diode Driver ............................................ Section 8
DH0035C PI N Diode Driver ........................................... Section 8
DM2502 Successive Approximation Register ........................... Section 2
DM2503 Successive Approximation Register ........................... Section 2
DM2504 Successive Approximation Register ........................... Section 2
DS0025C Two Phase MOS Clock Driver ................................ Section 5
DS0026 5 MHz Two Phase MOS Clock Driver ........................... Section 5
DS00565 MHz Two Phase MOS Clock Driver. .......................... Section 5
DS8187 Vacuum Fluorescent Display Driver ............................ Section 4
DS8615130 MHz Low Power Dual Modulus Prescaler ................... Section 6
DS8616 225 MHz Low Power Dual Modulus Prescaler ................... Section 6
DS8673 Low Power VHFfUHF Prescaler ............................... Section 6
DS8674 Low Power VHFfUHF Prescaler ............................... Section 6

xiii

Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
Data Acquisition
Data Acquisition
Data Acquisition
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific

Additional Available Linear Devices (Continued)
Dsa90aB AM/FM Digital Phase-Locked Loop Frequency Synthesizer ...... Section 6
DSa911 AM/FM/TV Sound Up-Conversion Frequency Synthesizer ........ Section 6
DSa913 AM/FM/TV Sound Up-Conversion Frequency Synthesizer ........ Section 6
DS55494 Hex Digit Driver ........................................... ; Section 4
DS75325 Memory Driver ............................................. Section 5
DS75361 Dual TIL-to-MOS Driver ..................................... Section 5
DS75365 Quad TTL-to-MOS Driver .................................... Section 5
DS75491 MOS-to-LED Quad Segment Driver ........................... Section 4
DS75492 MOS-to-LED Hex Digit Driver ................................ Section 4
DS75494 Hex Digit Driver ............................................ Section 4
LF111 Voltage Comparator ........................................... Section 3
LF147 Wide Bandwidth Quad JFET Input Operational Amplifier ............ Section 1
LF155 Series Monolithic JFET Input Operational Amplifiers .............•. Section 1
LF156 Series Monolithic JFET Input Operational Amplifiers ............... Section 1
LF157 Series Monolithic JFET Input Operational Amplifiers ............... Section 1
LF19a Monolithic Sample and Hold Circuit .............................. Section 6
LF211 Voltage Comparator .....................•..................... Section 3
LF29a Monolithic Sample and Hold Circuit. ............................. Section 6
LF311 Voltage Comparator .............................•...•......... Section 3
LF347 Wide Bandwidth Quad JFET Input Operational Amplifier ............ Section 1
LF351 Wide Bandwidth JFET Input Operational Amplifier ................. Section 1
LF353 Wide Bandwidth Dual JFET Input Operational Amplifier •.•......... Section 1
LF39aA Monolithic Sample and Hold Circuit ............................ Section 6
LF411 Low Offset, Low Drift JFET Input Operational Amplifier ............. Section 1
LF412 Low Offset, Low Drift Dual JFET Operational Amplifier .......•..... Section 1
LF441 Low Power JFET Input Operational Amplifier ..................... Section 1
LF442 Dual Low Power JFET Input Operational Amplifier ..........•...... Section 1
LF444 Quad Low Power JFET Input Operational Amplifier ................ Section 1
LF451 Wide-Bandwidth JFET Input Operational Amplifier .....•..•........ Section 1
LF453 Wide-Bandwidth Dual JFET Input Operational Amplifier ............ Section 1
LF11201 Quad SPST JFET Analog Switch .............................. Section a
LF11202 Quad SPST JFET Analog Switch ...................•.....•.... Section a
LF11331 Quad SPST JFET Analog Switch .............................. Section a
LF11332 Quad SPST JFET Analog Switch ...............•.............. Section a
LF11333 Quad SPST JFET Analog Switch .............................. Section a
LF13006 Digital Gain Set. ............................................ Section 6
LF13007 Digital Gain Set ..............................•........•..... Section 6
LF13201 Quad SPST JFET Analog Switch .............................. Section a
LF13202 Quad SPST JFET Analog Switch .....•..............•.•....... Section a
LF13331 Quad SPST JFET Analog Switch .............................. Section a
LF13332 Quad SPST JFET Analog Switch .......................•...... Section a
LF13333 Quad SPST JFET Analog Switch ....................•..•.•..•. Section a
LF1350a a-Channel Analog Multiplexer ...................•............ Section a
LF13509 4-Channel Analog Multiplexer ................................ Section a
LH0002 Buffer .....................................................• Section 2
LH0003 Wide Bandwidth Operational Amplifier .......................... Section 1
LH0004 High Voltage Operational Amplifier ............................. Section 1
* LH0020 High Gain Operational Amplifier ............................... Section 6
* LH0022 High Performance FET Operational Amplifier .................... Section 6
LH0023 Sample and Hold Circuit ...................................... Section 6
LH0024 High Slew Rate Operational Amplifier ........................•. Section 1
·See Appendix G

xiv

App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
OpAmps
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
OpAmps
OpAmps·
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
OpAmps

Additional Available Linear Devices (Continued)
LH0032 Ultra Fast FET-Input Operational Amplifier ...................... Section 1
LH0033 Fast and Ultra Fast Buffers ................................... Section 2
LH0036 Instrumentation Amplifier ..................................... Section 4
LH0041 0.2-Amp Power Operational Amplifier .......................... Section 1
LH0042 Low Cost FET Operational Amplifier ............................ Section 1
LH0043 Sample and Hold Circuit ...................................... Section 6
* LH0044 Series Precision Low Noise Operational Amplifiers ............... Section 6
* LH0052 Precision FET Operational Amplifier ............................ Section 6
LH0053 High Speed Sample and Hold Amplifier ......................... Section 6
* LH0061 0.5 Amp Wide Band Operational Amplifier ....................... Section 6
* LH0062 High Speed FET Operational Amplifier .......................... Section 6
LH0063 Fast and Ultra Fast Buffers ................................... Section 2
LH0070 Series BCD Buffered Reference ............................... Section 4
LH0071 Series Precision Buffered Reference ........................... Section 4
* LH0082 Optical Communication Receiver/Amplifier ..................... Section 6
* LH0086 Digitally-Programmable-Gain Amplifier .......................... Section 6
* LH0091 True RMS to DC Converter ............. '" ................... Section 10
LH0094 Multifunction Converter ....................................... Section 8
LH0101 Power Operational Amplifier ................................... Section 1
LH2003 100 MHz Video Line Driver .................................... Section 2
LH2033 100 MHz Video Line Driver .................................... Section 2
* LH21 01 A Dual High Performance Operational Amplifier .................. Section 6
* LH2108 Dual Super Beta Operational Amplifier .......................... Section 6
* LH211 0 Dual Voltage Follower ........................................ Section 6
LH2111 Dual Voltage Comparator ..................................... Section 3
* LH2201 A Dual High Performance Operational Amplifier .................. Section 6
* LH2210 Dual Voltage Follower ........................................ Section 6
* LH2301A Dual High Performance Operational Amplifier .................. Section 6
* LH2308 Dual Super Beta Operational Amplifier .......................... Section 6
* LH2310 Dual Voltage Follower ............................ '" ......... Section 6
LH2311 Dual Voltage Comparator ..................................... Section 3
LH4001 Wide band Current Buffer ..................................... Section 2
LH4002 Wide band Video Buffer ....................................... Section 2
* LH4003 Precision RF Closed Loop Buffer .............................. Section 6
* LH4006 Precision RF Closed Loop Buffer .............................. Section 6
* LH4008 Fast Buffer ................................................. Section 6
* LH4009 Fast Buffer ................................................. Section 6
* LH4010 Fast FET Buffer ............................................. Section 6
* LH4011 Fast Open Loop Buffer ....................................... Section 6
* LH4012 Wideband Buffer ............................................ Section 6
* LH4033C Fast and Ultra Fast Buffer Amplifiers .......................... Section 6
* LH4063C Fast and Ultra Fast Buffer Amplifiers .......................... Section 6
* LH4101 Wideband High Current Operational Amplifier ................... Section 6
LH41 04 G-MIL Fast Settling High Current Operational Amplifier ........... Section 1
* LH4105 Precision Fast Settling High Current Operational Amplifier ......... Section 6
* LH4106 ± 5V High Speed Operational Amplifier ......................... Section 6
* LH4117 Precision RF Amplifier ........................................ Section 6
LH4118 G-MIL Current Feedback Wide Band RF Amplifier ................ Section 1
* LH4124C High Slew Rate Operational Amplifier ......................... Section 6
* LH4141 C 0.2 Amp Power Operational Amplifier ......................... Section 6
* LH4161 High Speed Operational Amplifier .............................. Section 6
'See Appendix G

xv

OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
OpAmps
OpAmps
Data Acquisition
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
OpAmps
OpAmps
App. Specific
App. Specific
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps

Additional Available Linear Devices (Continued)
* LH4162 Dual High Speed Operational Amplifier ......................... Section 6

* LH4200 General Purpose GaAs FET Amplifier ...........•.............. Section 6
LH4266 SPDT RF Switch ............................................. Section 3
LH4860 Super Fast 12-Bit Track-Hold Amplifier ......................... Section 6
LH7070 Series Precision BCD Buffered Reference ...................... Section 4
LH7071 Series Precision Binary Buffered Reference ..............•...... Section 4
LM10 Operational Amplifier and Voltage Reference ...................... Section 1
LM 11 Operational Amplifier ........................................... Section 1
LM12L BOW Operational Amplifier .............................•...•... Section 1
LM34 Precision Fahrenheit Temperature Sensor ........................ Section 5
LM35 Precision Centigrade Temperature Sensor ...•.................... Section 5
LM101A Operational Amplifier .•..•.•..•.......•.....•.....•.......... Section 1
LM 102 Voltage Follower ............................................. Section 2
LM106 Voltage Comparator ..•.................•......•..•.....•..... Section 3
LM 107 Operational Amplifier .................................•.•••..•• Section 1
LM 108 Operational Amplifier .......................................... Section 1
LM110 Voltage Follower ............................................. Section 2
LM 111 Voltage Comparator .......................................... Section 3
LM 112 Operational Amplifier .......................................... Section 1
LM113 Reference Diode ..................................•.......... Section 4
LM 118 Operational Amplifier .......................................... Section 1
LM119 High Speed Dual Comparator .................................. Section 3
LM 122 Precision Timer .......................................•...... Section 8
LM124 Low Power Quad Operational Amplifier .......................... Section 1
LM129 Precision Reference .......................................... Section 4
LM131 Precision Voltage-to-Frequency Converter ....................... Section 2
LM134 3-Terminal Adjustable Current Source ........................... Section 4
LM 135 Precision Temperature Sensor ................................. Section 5
LM136-2.5V Reference Diode ........................................ Section 4
LM136-5.0V Reference Diode ........................................ Section 4
LM139 Low Power Low Offset Voltage Quad Comparator ................ Section 3
LM143 High Voltage Operational Amplifier .............................. Section 1
LM144 High Voltage, High Slew Rate Operational Amplifier ............... Section 1
LM146 Programmable Quad Operational Amplifier ....................... Section 1
LM 148 Quad 741 Operational Amplifier ................................ Section 1
LM149 Wide Band Decompensated (Av(MIN) = 5) ...................... Section 1
LM 158 Low Power Dual Operational Amplifier ....•...................... Section 1
LM160 High Speed Differential Comparator ............................. Section 3
LM161 High Speed Differential Comparator ............................. Section 3
LM168 Precision Voltage Reference .............................•..... Section 4
LM169 Precision Voltage Reference ....•........................•..... Section 4
LM185 Adjustable Micropower Voltage Reference ..........•.....•...... Section 4
LM185-1.2 MicropowerVoltage Reference Diode ....................... Section 4
LM185-2.5 Micropower Voltage Reference Diode ....................... Section 4
LM193 Low Power Low Offset Voltage Dual Comparator ................. Section 3
LM194 Supermatch Pair .............................•...•...•...•... Section 1
LM 194 SuperMatch Pair ............................................. Section B
LM195 Ultra Reliable Power Transistor ................................. Section 8
LM199 Precision Reference ............... r.- • •••••••••••••••••••••••• Section 4
LM201 A Operational Amplifier .................•...................... Section 1
LM207 Operational Amplifier .......................................... Section 1
"Sea Appendix G

xvi

OpAmps
OpAmps
App. Specific
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
OpAmps
OpAmps
App. Specific
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
OpAmps
App. SpecifiC
App. Specific
Data Acquisition
OpAmps
OpAmps

Additional Available Linear Devices(continUed)
LM208 Operational Amplifier .......................................... Section 1
LM210 Voltage Follower ................. " .......................... Section 2
LM211 Voltage Comparator .......................................... Section 3
LM212 Operational Amplifier .......................................... Section 1
LM218 Operational Amplifier .......................................... Section 1
LM219 High Speed Dual Comparator .................................. Section 3
LM221 Precision Preamplifier ......................................... Section 4
LM224 Low Power Quad Operational Amplifier .......................... Section 1
LM231 Precision Voltage-to-Frequency Converter ....................... Section 2
LM234 3-Terminal Adjustable Current Source ........................... Section 4
LM235 Precision Temperature Sensor ................................. Section 5
LM236-2.5V Reference Diode ........................................ Section 4
LM236-5.0V Reference Diode ........................................ Section 4
LM239 Low Power Low Offset Voltage Quad Comparator ................ Section 3
LM246 Programmable Quad Operational Amplifier ....................... Section 1
LM248 Quad 741 Operational Amplifier ................................ Section 1
LM258 Low Power Dual Operational Amplifier ........................... Section 1
LM261 High Speed Differential Comparator ............................. Section 3
LM268 Precision Voltage Reference ................................... Section 4
LM285 Adjustable Micropower Voltage Reference ....................... Section 4
LM285-1.2 Micropower Voltage Reference Diode ....................... Section 4
LM285-2.5 Micropower Voltage Reference Diode ....................... Section 4
LM293 Low Power Low Offset Voltage Dual Comparator ................. Section 3
LM295 Ultra Reliable Power Transistor ................................. Section 8
LM299 Precision Reference .......................................... Section 4
LM301 A Operational Amplifier ........................................ Section 1
LM302 Voltage Follower .................................... " .... " . Section 2
LM306 Voltage Comparator .......................................... Section 3
LM307 Operational Amplifier .......................................... Section 1
LM308 Operational Amplifier .......................................... Section 1
LM310 Voltage Follower ............................................. Section 2
LM311 Voltage Comparator .......................................... Section 3
LM312 Operational Amplifier .......................................... Section 1
LM313 Reference Diode ............................................. Section 4
LM318 Operational Amplifier .......................................... Section 1
LM319 High Speed Dual Comparator .................................. Section 3
LM321 Precision Preamplifier ......................................... Section 4
LM322 Precision Timer .............................................. Section 8
LM324 Low Power Quad Operational Amplifier .......................... Section 1
LM329 Precision Reference .......................................... Section 4
LM331 Precision Voltage-to-Frequency Converter ....................... Section 2
LM334 3-Terminal Adjustable Current Source ........................... Section 4
LM335 Precision Temperature Sensor ................................. Section 5
LM336-2.5V Reference Diode ........................................ Section 4
LM336-5.0V Reference Diode ........................................ Section 4
LM339 Low Power Low Offset Voltage Quad Comparator ................ Section 3
LM343 High Voltage Operational Amplifier .............................. Section 1
LM344 High Voltage, High Slew Rate Operational Amplifier ............... Section 1
LM346 Programmable Quad Operational Amplifier ....................... Section 1
LM348 Quad 741 Operational Amplifier ................................ Section 1
LM349 Wide Band Decompensated (Av(MIN) = 5) ...................... Section 1
'See Appendix G

xvii

OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
App. Specific
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
OpAmps
OpAmps
OpAmps
App. Specific
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps

Additional Available Linear Devices (Continued)
LM358 Low Power Dual Operational Amplifier ........................... Section 1
LM359 Dual, High Speed, Programmable Current Mode (Norton) Amplifier .. Section 1
LM360 High Speed Differential Comparator ............................. Section 3
LM361 High Speed Differential Comparator ............................. Section 3
LM368 Precision Voltage Reference ................................... Section 4
LM368-2.5 Precision Voltage Reference ............................... Section 4
LM369 Precision Voltage Reference ................................... Section 4
LM380 Audio Power Amplifier ......................................... Section 1
LM383 7 Watt Audio Power Amplifier .................................. Section 1
LM384 5 Watt Audio Power Amplifier .................................. Section 1
LM385 Adjustable Micropower Voltage Reference ....................... Section 4
LM385-1.2 Micropower Voltage Reference Diode ....................... Section 4
LM385-2.5 Micropower Voltage Reference Diode ....................... Section 4
LM386 Low Voltage Audio Power Amplifier ............................. Section 1
LM388 1.5-WaU Audio Power Amplifier ................................. Section 1
LM389 Low Voltage Audio Power Amplifier with NPN Transistor Array ...... Section 1
LM390 1 Watt Battery Operated Audio Power Amplifier ................... Section 1
LM391 Audio Power Driver .................. , ....•................... Section 1
LM392 Low Power Operational AmplifierlVoltage Comparator ............ Section 1
LM393 Low Power Low Offset Voltage Dual Comparator ................. Section 3
LM394 Supermatch Pair ............................................. Section 1
LM394 SuperMatch Pair ............................................. Section 8
LM395 Ultra Reliable Power Transistor ................................. Section 8
LM399 Precision Reference .......................................... Section 4
LM555 Timer ....................................................... Section 8
LM555C Timer ...................................................... Section 8
LM556 Dual Timer ................................................... Section 8
LM556C Dual Timer ................................................. Section 8
LM565 Phase Locked Loop ........................................... Section 8
LM565C Phase Locked Loop ......................................... Section 8
LM566C Voltage Controlled Oscillator ................................. Section 8
LM567 Tone Decoder ............................................... Section 8
LM567C Tone Decoder .............................................. Section 8
LM604 4-Channel MUX-Amp ......................................... Section 1
LM607 Precision Operational Amplifier ................................. Section 1
LM611 Operational Amplifier and Adjustable Reference .................. Section 1
LM612 Dual-Channel Comparator and Reference ....................... Section 3
LM613 Dual Operational Amplifier, Dual Comparator, and Adjustable
Reference ....................................................... Section 3
LM613 Dual Operational Amplifier, Dual Comparator, and Adjustable
Reference ....................................................... Section 1
LM614 Quad Operational Amplifier and Adjustable Reference ............. Section 1
LM615 Quad Comparator and Adjustable Reference ..................... Section 3
LM627 Precision Operational Amplifier ................................. Section 1
LM637 Precision Operational Amplifier ................................. Section 1
LM675 Power Operational Amplifier ................................... Section 1
LM709 Operational Amplifier .......................................... Section 1
LM710 Voltage Comparator .......................................... Section 3
LM715 High Speed Operational Amplifier ............................... Section 1
LM725 Operational Amplifier .................. : ....................... Section 1
LM741 Operational Amplifier .......................................... Section 1
'See Appendix G

xviii

OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
App. Specific
App. Specific
App. Specific
Data Acquisition
Data Acquisition
Data Acquisition
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
OpAmps
App. Specific
App. Specific
Data Acquisition
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
OpAmps
OpAmps
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OpAmps
OpAmps
OpAmps
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Additional Available Linear Devices(continUed)
LM747 Dual Operational Amplifier ..................................... Section 1
LM748 Operational Amplifier .......................................... Section 1
LM759 Power Operational Amplifier ................................... Section 1
LM760 High Speed Differential Comparator ............................. Section 3
LM831 Low Voltage Audio Power Amplifier ............................. Section 1
LM832 Dynamic Noise Reduction System DNR ......................... Section 1
LM833 Dual Audio Operational Amplifier ............................... Section 1
LM837 Low Noise Quad Operational Amplifier .......................... Section 1
LM903 Fluid Level Detector .......................................... Section 7
LM1035 Dual DC Operated TonelVolume/Balance Circuit. ............... Section 1
LM1036 Dual DC Operated TonelVolume/Balance Circuit. ............... Section 1
LM1037 Dual Four-Channel Analog Switch ............................. Section 1
LM1040 Dual DC Operated TonelVolume/Balance Circuit with Stereo
Enhancement Facility .............................................. Section 1
LM1042 Fluid Level Detector ......................................... Section 7
LM 1044 Analog Video Switch ......................................... Section 3
LM1131A Dual Dolby B-Type Noise Reduction Processor ................ Section 1
LM1151 Dolby B-Type Noise Reduction System ......................... Section 1
LM1201 Video Amplifier System ....................................... Section 3
LM1201 Video Amplifier System ....................................... Section 1
LM1202 230 MHz Video Amplifier System .............................. Section 1
LM1202 230 MHz Video Amplifier System .............................. Section 3
LM1203 RGB Video Amplifier System .................................. Section 3
LM 1203 RG B Video Amplifier System .................................. Section 1
LM1203A 150 MHz RGB Video Amplifier System ........................ Section 1
LM1203A 150 MHz RGB Video Amplifier System ........................ Section 3
LM1203B 100 MHz RGB Video Amplifier System ........................ Section 3
LM1204 150 MHz RGB Video Amplifier System ......................... Section 3
LM1211 Broadband Demodulator System .............................. Section 2
LM 1391 Phase-Locked Loop ......................................... Section 3
LM1414 Dual Differential Voltage Comparator .......................... Section 3
LM1458 Dual Operational Amplifier .................................... Section 1
LM1496 Balanced Modulator-Demodulator ............................. Section 2
LM 1558 Dual Operational Amplifier .................................... Section 1
LM1596 Balanced Modulator-Demodulator ............................. Section 2
LM1801 Battery Operated Power Comparator ........................... Section 3
LM 1815 Adaptive Sense Amplifier ..................................... Section 7
LM1819 Air-Core Meter Driver ........................................ Section 7
LM1823 Video IF Amplifier/PLL Detector System ........................ Section 3
LM 1830 Fluid Detector ............................................... Section 7
LM1851 Ground Fault Interrupter ...................................... Section 8
LM1865 Advanced FM IF System ..................................... Section 2
LM1868 AM/FM Radio System ....................................... Section 2
LM1875 20 Watt Power Audio Amplifier ................................ Section 1
LM1875 20 Watt Power Audio Amplifier ................................ Section 1
LM1877 Dual Power Audio Amplifier ................................... Section 1
LM 1877 Dual Power Audio Amplifier ................................... Section 1
LM1881 Video Sync Separator ........................................ Section 3
LM1882 Programmable Video Sync Generator .......................... Section 3
LM1894 Dynamic Noise Reduction System DNR ........................ Section 1
LM 1896 Dual Power Audio Amplifier ................................... Section 1
*See Appendix G

xix

OpAmps
OpAmps
OpAmps
OpAmps
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
App. Specific
App. Specific
OpAmps
OpAmps
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
App. Specific
OpAmps
App. Specific
OpAmps
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific

Additional Available linear Devices (Continued)
LM1921 1 Amp Industrial Switch ...................................... Section 7
LM1946 Over/Under Current Limit Diagnostic Circuit. .................... Section 7
LM1949 Injector Drive Controller ...................................... Section 7
LM1950 750 mA High Side Switch ..................................... Section 7
LM1951 Solid State 1 Amp Switch ..................................... Section 7
LM 1964 Sensor Intertace Amplifier .................................... Section 7
LM2240 Programmable Timer/Counter ................................ Section 8
LM2416 Triple 50 MHz CRT Driver ............................ ; ....... Section 3
LM2416C Triple 50 MHz CRT Driver ................................... Section 3
LM2418 Triple 30 MHz CRT Driver .................................... Section 3
LM2419 Triple 65 MHz CRT Driver .................................... Section 3
LM2877 Dual 4 Watt Power Audio Amplifier ............................. Section 1
LM2877 Dual 4 Watt Power Audio Amplifier ............................. Section 1
LM2878 Dual 5 Watt Power Audio Amplifier ............................. Section 1
LM2878 Dual 5 Watt Power Audio Amplifier ............................. Section 1
LM2879 Dual 8 Watt Audio Amplifier ................................... Section 1
LM2879 Dual 8 Watt Audio Amplifier ................................... Section 1
LM2896 Dual Power Audio Amplifier ................................... Section 1
LM2900 Quad Amplifier .............................................. Section 1
LM2901 Low Power Low Offset Voltage Quad Comparator ............... Section 3
LM2902 Low Power Quad Operational Amplifier ...................... ; .. Section 1
LM2903 Low Power Low Offset Voltage Dual Comparator ................ Section 3
LM2904 Low Power Dual Operational Amplifier .......................... Section 1
LM2907 Frequency to Voltage Converter ............................... Section 8
LM2917 Frequency to Voltage Converter ............................... Section 8
LM2924 Low Power Operational AmplifierlVoltage Comparator ........... Section 1
. LM3045 Transistor Array ............................................. Section 8
LM3046 Transistor Array ............................................. Section 8
LM3080 Operational Transconductance Amplifier ....................... Section 1
LM3086 Transistor Array ............................................. Section 8
LM3089 FM Receiver IF System ...................................... Section 2
LM3146 High Voltage Transistor Array ................................. Section 8
LM3189 FM IF System ............................................... Section 2
LM3301 Quad Amplifier .............................................. Section 1
LM3302 Low Power Low Offset Voltage Quad Comparator ............... Section 3
LM3303 Quad Operational Amplifier ................................... Section 1
LM3361 A Low Voltage/Power Narrow Band FM IF System ............... Section 2
LM3403 Quad Operational Amplifier ................................... Section 1
LM3875 High Pertormance 40 Watt Audio Power Amplifier ................ Section 1
LM3875 High Pertormance 40 Watt Audio Power Amplifier ................ Section 1
LM3876 High Pertormance 40 Watt Audio Power Amplifier ................ Section 1
LM3900 Quad Amplifier .............................................. Section 1
LM3905 Precision Timer ............................................. Section 8
LM3909 LED Flasher/Oscillator ....................................... Section 4
LM3911 Temperature Controller ...................................... Section 5
LM3914 Dot/Bar Display Driver ....................................... Section 4
LM3915 Dot/Bar Display Driver .......................... '............. Section 4
LM3916 Dot/Bar Display Driver ....................................... Section 4
LM3999 Precision Reference ......................................... Section 4
LM4040 Precision Micropower Shunt Voltage Reference ................. Section 4
LM4041 Precision Micropower Shunt Voltage Reference ................. Section 4
'See Appendix G

xx

App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
App. Specific
App. Specific
OpAmps
App. Specific
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
App. Specific
App. Specific
OpAmps
App. Specific
App. Specific
OpAmps
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
OpAmps
App. Specific
OpAmps
OpAmps
App. Specific
App. Specific
OpAmps
App. Specific
App. Specific
Data Acquisition
App. Specific
App. Specific
App. Specific
Data Acquisition
Data Acquisition
Data Acquisition

Additional Available Linear Devices (Continued)
LM4136 Quad Operational Amplifier ................................... Section 1
LM4250 Programmable Operational Amplifier ........................... Section 1
LM4431 Micropower Shunt Voltage Reference .......................... Section 4
LM6118 Fast Settling Dual Operational Amplifier ........................ Section 1
LM6121 High Speed Buffer ........................................... Section 2
LM6125 High Speed Buffer ........................................... Section 2
LM6161 High Speed Operational Amplifier .............................. Section 1
LM6162 High Speed Operational Amplifier .............................. Section 1
LM6164 High Speed Operational Amplifier .............................. Section 1
LM6165 High Speed Operational Amplifier .............................. Section 1
LM6181 100 mA, 100 MHz Current Feedback Amplifier .................. Section 1
LM6218 Fast Settling Dual Operational Amplifier ........................ Section 1
LM6221 High Speed Buffer ........................................... Section 2
LM6225 High Speed Buffer ........................................... Section 2
LM6261 High Speed Operational Amplifier .............................. Section 1
LM6262 High Speed Operational Amplifier .............................. Section 1
LM6264 High Speed Operational Amplifier .............................. Section 1
LM6265 High Speed Operational Amplifier .............................. Section 1
LM6313 High Speed, High Power Operational Amplifier .................. Section 1
LM6321 High Speed Buffer ........................................... Section 2
LM6325 High Speed Buffer ........................................... Section 2
LM6361 High Speed Operational Amplifier .............................. Section 1
LM6362 High Speed Operational Amplifier .............................. Section 1
LM6364 High Speed Operational Amplifier .............................. Section 1
LM6365 High Speed Operational Amplifier .............................. Section 1
LM6685 Ultra Fast Single Latched Comparator .......................... Section 3
LM6687 Ultra Fast Voltage Comparator ................................ Section 3
LM9140 Precision Micropower Shunt Voltage Reference ................. Section 4
LM1245412-Bit + Sign Data Acquisition System with Self-Calibration ..... Section 1
LM 12458 12-Bit + Sign Data Acquisition System with Self-Calibration ..... Section 1
LM 13080 Programmable Power Operational Amplifier .................... Section 1
LM 13600 Dual Operational Transconductance Amplifier with Linearizing
Diodes and Buffers ................................................ Section 1
LM77000 Power Operational Amplifier ................................. Section 1
LMC555 CMOS Timer ............................................... Section 8
LMC567 Low Power Tone Decoder .................................... Section 8
LMC568 Low Power Phase-Locked Loop ............................... Section 8
LMC660 CMOS Quad Operational Amplifier ............................ Section 1
LMC662 CMOS Dual Operational Amplifier ............................. Section 1
LMC835 Digital Controlled Graphic Equalizer ........................... Section 1
LMC1982 Digitally-Controlled Stereo Tone and Volume Circuit with Two
Selectable Stereo Inputs ........................................... Section 1
LMC1983 Digitally-Controlled Stereo Tone and Volume Circuit with Three
Selectable Stereo Inputs ........................................... Section 1
LMC1992 Digitally-Controlled Stereo Tone and Volume Circuit with
Four-Channel Input-Selector ........................................ Section 1
LMC6022 Micropower CMOS Dual Operational Amplifier ................. Section 1
LMC6024 Micropower CMOS Quad Operational Amplifier ................ Section 1
LMC6032 CMOS Dual Operational Amplifier ............................ Section 1
LMC6034 CMOS Quad Operational Amplifier ........................... Section 1
LMC6041 CMOS Single Micropower Operational Amplifier ................ Section 1
'See Appendix G

xxi

OpAmps
OpAmps
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
OpAmps
OpAmps
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps

Additional Available Linear Devices (Continued)
LMC6042 CMOS Dual Micropower Operational Amplifier ................. Section 1
LMC6044 CMOS Quad Micropower Operational Amplifier ................ Section 1
LMC6061 Precision CMOS Single Micropower Operational Amplifier ....... Section 1
LMC6062 Precision CMOS Dual Micropower Operational Amplifier ........ Section 1
LMC6064 Precision CMOS Quad Micropower Operational Amplifier ........ Section 1
LMC6081 Precision CMOS Single Operational Amplifier .................. Section 1
LMC6082 Precision CMOS Dual Operational Amplifier ................... Section 1
LMC6084 Precision CMOS Quad Operational Amplifier ................... Section 1
LMC6482 CMOS Dual Rail-to-Raillnput and Output Operational Amplifier .. Section 1
LMC6484 CMOS Quad Rail-to-Raillnput and Output Operational Amplifier .. Section 1
LMD18400 Quad High Side Driver ..................................... Section 7
LMF40 High Performance 4th-Order Switched Capacitor Butterworth
Low-Pass Filter ................................................... Section 7
LMF60 High Performance 6th-Order Switched Capacitor Butterworth
Low-Pass Filter ................................................... Section 7
LMF90 4th-Order Elliptic Notch Filter .................................. Section 7
LMF100 High Performance Dual Switched Capacitor Filter ................ Section 7
LMF120 Mask Programmable Switched Capacitor Filter .................. Section 7
LMF380 Triple One-Third Octave Switched Capacitor Active Filter ......... Section 7
LP124 Low Power Quad Operational Amplifier .......................... Section 1
LP265 Micropower Programmable Quad Comparator .................... Section 3
LP311 Voltage Comparator ........................................... Section 3
LP324 Low Power Quad.Operational Amplifier .......................... Section 1
LP339 Ultra-Low Power Quad Comparator .............................. Section 3
LP365 Micropower Programmable Quad Comparator .................... Section 3
LP395 Ultra Reliable Power Transistor ................................. Section 8
LP2902 Low Power Quad Operational Amplifier ......................... Section 1
LPC660 Low Power CMOS Quad Operational Amplifier .................. Section 1
LPC661 Low Power CMOS Operational Amplifier ........................ Section 1
LPC662 Low Power CMOS.Dual Operational Amplifier ................... Section 1
MF4 4th Order Switched Capacitor Butterworth Lowpass Filter ............ Section 7
MF5 Universal Monolithic Switched Capacitor Filter ...................... Section 7
MF6 6th Order Switched Capacitor Butterworth Lowpass Filter ............ Section 7
MF8 4th Order Switched Capacitor Bandpass Filter ...................... Section 7
MF10 Universal Monolithic Dual Switched Capacitor Filter ................ Section 7
* MH0007 DC Coupled MOS Clock Driver ................................ Section 10
* MH0007C DC Coupled MOS Clock Driver .............................. Section 10
MM54C905 12-Bit Successive Approximation Register ................... Section 2
MM54HC4016 Quad Analog Switch ................................... Section 8
MM54HC4051 8-Channel Analog Multiplexer ........................... Section 8
MM54HC4052 Dual4-Channel Analog Multiplexer ....................... Section 8
MM54HC4053 Triple 2-Channel Analog Multiplexer ..... " ............... Section 8
MM54HC4066 Quad Analog Switch ................................... Section 8
MM54HC4316 Quad Analog Switch with Level Translator ................ Section 8
MM74C905 12-Bit Successive Approximation Register ................... Section 2
MM74HC4016 Quad Analog Switch ................................... Section 8
MM74HC4051 8-Channel Analog Multiplexer ........................... Section 8
MM74HC4052 Dual4-Channel Analog Multiplexer ....................... Section 8
MM74HC4053 Triple 2-Channel Analog Multiplexer ...................... Section 8
MM74HC4066 Quad Analog Switch ................................... Section 8
MM74HC4316 Quad Analog Switch with Level Translator ................ Section 8
"See Appendix G

xxii

OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
App. Specific
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
OpAmps
App. Specific
OpAmps
OpAmps
OpAmps
OpAmps
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
App. Specific
App. Specific
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition
Data Acquisition

Additional Available Linear

Devices(continUed)

MM5368 CMOS Oscillator Divider Circuit ............................... Section 6
MM5369 Series 17 Stage Oscillator/Divider ............................ Section 6
MM5437 Digital Noise Source ......................................... Section 6
MM5450 LED Display Driver .......................................... Section 4
MM5451 LED Display Driver .......................................... Section 4
MM5452 Liquid Crystal Display Driver .................................. Section 4
MM5453 Liquid Crystal Display Driver .................................. Section 4
MM5480 LED Display Driver .......................................... Section 4
MM5481 LED Display Driver .......................................... Section 4
MM5483 Liquid Crystal Display Driver .................................. Section 4
MM5484 16-Segment LED Display Driver ............................... Section 4
MM5486 LED Display Driver .......................................... Section 4
MM58201 Multiplexed LCD Driver ..................................... Section 4
MM58241 High Voltage Display Driver ................................. Section 4
MM58242 High Voltage Display Driver ................................. Section 4
MM58248 High Voltage Display Driver ................................. Section 4
MM58341 High Voltage Display Driver ................................. Section 4
MM58342 High Voltage Display Driver ................................. Section 4
MM58348 High Voltage Display Driver ................................. Section 4
OP07 Low Offset, Low Drift Operational Amplifier ........................ Section 1
TL081 Wide Bandwidth JFET Input Operational Amplifier ................. Section 1
TL082 Wide Bandwidth Dual JFET Input Operational Amplifier ............ Section 1

·See Appendix G

xxiii

App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
App. Specific
OpAmps
OpAmps
OpAmps

..

II)

.Q

E
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~National

Semiconductor

ca
D.
>.Q
II)
(.)

Cross Reference by Part Number

..

II)

A complete interchangeability list of Linear IC's offered by most Integrated Circuit Manufacturers is listed in this section, and
references the nearest National Semiconductor Corporation direct replacement or recommended replacement with either an
improved or functional replacement.

II)

The following companies are included in this cross reference:

c

II)

a:
en
en

e

0

Harris (GE/RCA/lntersil)
Hitachi
Linear Technology Corp.
Maxim
Motorola

Analog Devices
Burr Brown
Cherry
Elantec
Fairchild (NSC)

Part Number

NSC
Part Number

Part Number

Philips
Precision Monolithics Inc.
Raytheon
Samsung
SGS Thompson

NSC
Part Number

Part Number

Signetics
Siliconix
Texas Instruments
Toshiba
Unitrode

NSC
Part Number

ANALOG DEVICES
ADOO42
AD101A
AD201A
AD301A
AD5035

LHOO42
LM101A
LM201A
LM301A
LHOO42

LM135
LM34
LM35
LF441
LM363

S
S
S

I
S

AD590
AD590
AD590
AD611
AD624

AD506
AD509
AD521
AD521
AD522

LHOO22
LHOOO3
LHOO36
LM363
LHOO38

S
S
S
S
S

AD650
AD651
AD654
AD673
AD707

LM331
LM331
LM331
ADC0841
LM607

AD524
AD537
AD546
AD546
AD548

LM363
LM331
LPC660
LPC662
LF441

S
S
I
D

AD711
AD712
AD741
AD746
AD7502

AD549
AD549
AD562
AD563
AD565A

LPC660
LPC662
DAC1266
DAC1265
DAC1265

I
S
S
S

AD566A
AD567
AD573
AD581
AD582

DAC1266
DAC1230
ADC1005
LHOO70
LF398

S
S
S

AD583
AD588
AD589M
AD589U
AD590

LF398
LM369
LM385
LM185
LM134

S
S

S

S

AD7542
AD7545
AD7545
AD7545
AD7548

DAC1210
DAC1208
DAC1209
DAC1210
DAC1230

S
S
S
S
S

S
S
S
S

AD7548
AD7548
AD7552
AD7552
AD7575

DAC1231
DAC1232
ADC1220
ADC1225
ADC0820

S
S
S
S
S

LF411
LF412
LM741
LM6218
LF13509

S
S
D
I
S

AD7576
AD7578
AD7578
AD7820
AD7821

ADC0820
ADC1205
ADC1225
ADC0820
ADC08061

S
S
S
D

AD7523
AD7523
AD7523
AD7524
AD7524

DAC0830
DAC0831
DAC0832
DAC0830
DAC0831

S
S
S
S
S

AD7824
AD7828
AD844
AD846
AD847

ADC08064
ADC08068
LM6181
LM6181
LM6161

AD7524
AD7533
AD7533
AD7533
AD7541

DAC0832
DAC1020
DAC1021
DAC1022
DAC1218

S
D
D
D
S

AD848
AD849
AD96685
AD96687
ADDAC-08

LM6164
LM6165
LM6685
LM6687
DAC0800

D

AD7541
AD7541A
AD7541A
AD7542
AD7542

DAC1219
DAC1218
DAC1219
DAC1208
DAC1209

S
S
S
S
S

ADDAC-08
ADDAC-08
ADOP07
HTC-0300

DAC0801
DAC0802
LM607
LH4860

D
D
I
S

S

The following notations are appended to assist you In finding the best option.

S

~

NSC Similar Device

I

~

NSC Improved Device

xxiv

D

~

NSC Direct Replacement

D
D
D

..

(")

Part Number

NSC
Part Number

Part Number

NSC
Part Number

Part Number

BURR·BROWN

0

NSC
Part Number

0
0

CHERRY

3507
3507
3507
3507
3510

LHOO03
LMl18
LM6361
LM709
LM101

S
S
S
S
S

OPA111
OPA121
OPA121
OPA121
OPA156

LH0052
LF441 A
LH0022
LH0042
LF156

S
S
S
S
S

3510
3510
3510
3510
3533

LM107
LMl12
LM725
LM748
LH0033

S
S
S
S
S

OPA21
OPA21
OPA2111
OPA21ll
OPA21ll

LM108A
LM11
LF353
LF412A
LF442A

S
S
S
S
S

3542
3550
3551
3551
3553

LH0042
LM6361
LH0024
LM6361
LHOO02

S
S
S
S
S

OPA21ll
OPA21ll
OPA2111
OPA2111
OPA21ll

LH2011
LH2101A
LH2108A
LM1558
LM358

S
S
S
S
S

3553
3554
3571
3572
3573

LH0063
LH0032
LM675
LH0021
LM675

S
S
S
S
S

OPA2ll1
OPA2111
OPA27
OPA27
OPA37

LM2904
LM747A
LHOO44
LM627
LM637

S
S
S
S
S

3580
3580
3580
3606A6
3606A6

LHOO04
LM143
LM144
LH0084
LH0086

S
S
S
S
S

OPA404
OPA404
OPA404
OPA511
OPA541

LF444A
LM837
LMC660
LM675
LH0101

S
S
S
S
S

3626
3629
ADC80
DAC7541A
DAC7541A

LH0036
LH0038
ADC1280
AD7521
AD7531

S
S
S
S
S

OPA541
OPA602
OPA605
OPA605
OPA633

LM12
LF411
LHOO05
LH0032
LH0033

S
S
S
S
S

DAC7541A
DAC7541A
DAC811
HOS·l00
HI-508

DAC1218
DAC1219
ADC1230
LH0033
LF13508

S
S
S
S
S

OPA633
PGA100/102
PGA200/201
SHC298
SHC298

LH4001
LH0086
LH0084
LF298
LH0043

S
S
S
D
S

HI-509
INA101
INA101HP
INA102
INA102

LF13509
LM163
LM363
LH0038
LM363

S
S
S
S
S

SHC5320
SHC80
SHC85
SHC85
VFC32

LH0053
LF398
LF398
LH0053
LM131/331

D
S
S
S
S

CS·189
CS-2907
CS-2917
CS-925
CS-935

= NSC Similar Device

I

= NSC Improved Device

xxv

D

S
D
D
S
S

EHA2500
EHA2502
EHA2505
EHA2510
EHA2512

LM6161
LM6l61
LM6361
LM6l61
LM6l61

S
S
S
S
S

EHA2515
EHA2520
EHA2522
EHA2525
EHA2600

LM6361
LM6164
LM6164
LM6364
LM6161

S
S
S
S
S

EHA2602
EHA2605
EHA2620
EHA2622
EHA2625

LM6161
LM6361
LM6164
LM6164
LM6364

S
S
S
S
S

EL2006
EL2006C
EL2020
ELHOO02
ELH0021

LM6161
LM6261
LM6181
LHOO02
LH002l

S
S
I
D
D

ELH0032
ELH0033
ELH0041
ELH0101

LH0032
LH0033
LH0041
LH0101

D
D
D
D

= NSC Direct Replacement

C'D
C'D
C'D

::s
n

C'D

cr

'<

-.
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I»

Z

ELANTEC

llIe following notations are appended to aaslst you In finding the best option.
S

LM1819
LM2907
LM2917
LM2925
LM2935

-..
::D

c
cr

3

..
C'D

...
CP

J:I

E

Part Number

1::
as

FAIRCHILD (N5C)

Z

0..

~
CP

()

C

...

CP
CP

';

a:

In
In

e

(.)

N~C

NSC
Part Number

:::I

Part Number

Part Number

Part Number

NSC
Part Number

JLA101
,.A105
,.A108
JLA108A
,.A110

LM101
LM105
LM108
LM108A
LM110

D
D
D
D
D

,.A5156
,.A555
,.A556
,.A5800
,.A709

TP5156
LM555
LM556
TP3204
LM709

D
D
D
b
D

JLA78M12
p.A78MXX
}lA78MXX
p.A18XX
,.A78XX

LM78M12
LM341-XX
LM78MXX
LM140-XX
LM340-XX

D
D
D
D
D

,.A111
,.A117
,.A124
,.A139
,.A1458

LM111
LM117
. LM124
LM139
LM1458

D
D
D
D
D

,.A71 0
,.A711
,.A723
,.A725
,.A741

LM710
LM711
LM723
LM725
LM741

D
D
D
D
D

p,A78XX
,.A790S
,.A7912
p,A7915
,.A79M05

LM78XX
LM7905
LM7912
LM7915
LM79M05

D
D
D
D
D

,.A1489
,.A1558
,.A201
,.A208
,.A208A

D51489
LM1558
LM201
LM208
LM208A

D
D
D
D
D

,.A747
,.A748
,.A75107
,.A75108
,.A75150

LM747
LM748
D575107
D575108
D575150

D
D
D
D
D

p,A79M12
,.A79M15
,.A79MXX
,.A79XX
,.A79XX

LM79M12
LM79M15
LM320-XX
LM320-XX
LM79LXX

D
D
D
D
D

,.A2111
,.A224
,.A239
,.A26L531
,.A26L532

LH2111
LM224
LM239
D526L531
D526L532

D
D
D
D
D

,.A75154
,.A75450
,.A75491
,.A760
,.A771

D575154
D575450
D575491
LM760
LF351

D
D
D
D
D

,.A79XX
,.A79XX
DAC1508
5HOO02
5H1605

LM79MXX
LM79XX
MC1508
LHOO02
LH1605

D
D
D
D
D

,.A2901
,.A301
,.A301A
,.A305
,.A3052

LM2901
LM301
LM301A
LM305
TP3052

D
D
D
D
D

,.A772
,.A774
,.A7805
JLA7805
JLA7805

LF353
LF347
LM140
LM340-5
LM7805

D
D
D
D
D

JLA305A
,.A308
,.A3086
,.A30554
,.A30557

LM305A
LM308
LM3086
TP3054
TP3057

D
D
D
D
D

,.A7806
,.A7808
,.A7812
,.A7812
,.A7812

LM7806
LM7808
LM140
LM340-12
LM7812

D
D
D
D
D

JLA30564
,.A30567
,.A311
,.A317
,.A324

TP3064
TP3067
LM311
LM317
LM324

D
D
D
D
D

,.A7815
,.A7815
,.A7815
,.A7818
,.A7824

LM140
LM340-15
LM7815
LM7818
LM7824

D
D
D
D
D

,.A3302
,.A348
,.A3486
,.A350
,.A5116

LM3302
LM348
D53486
LM350
TP5116

D
D
D
D
D

,.A78L05
,.A78L12
,.A78L15
,.A78LXXA
,.A78M05

LM78L05
LM78L12
LM78L15
LM78LXXA
LM78M05

D
D
D
D
D

HARRIS (GE/RCAllntersiI)
,.A748
AD7520
Ab7520
AD7521
AD7521

LM748
DAC1021
DAC1022
DAC1220
DAC1221

D
D
D
D
D

AD7521
AD7530
AD7530
AD7530
AD7531

DAC1222
DAC1020
DAC1021
DAC1022
DAC1220

D
5
5
5
D

AD7531
AD7531
AD7533
AD7533
AD7533

DAC1221
DAC1222
DAC1020
DAC1021
DAC1022

D
D
D
D
D

AD7541
AD7541
ADC0801
ADC0802
ADC0803

DAC1218
DAC1219
ADC0801
ADC0802
ADC0803

5
5
D
D
D

The following notations are appended to aulat you In finding the beat option.
S

~

NSC Similar Device

I

~

NSC Improved Device

xxvi

D

~

NSC Direct Replacement

Part Number

NSC
Part Number

Part Number

HARRIS (GE/RCAllntersil)
(Continued)
ADCOB04
CAOB1
CAOB1
CAOB2
CAOB2

ADCOB04
LF411
TLOB1
LF412
TLOB2

0
S
0
S
0

CAOB4
CAOB4
CA124
CA139
CA139A

LF147
LF347
LM124
LM139
LM139A

S
S
0
0
0

CA145B
CA155B
CA15B
CA15BA
CA224

LM145B
LM155B
LM15B
LM15BA
LM224

0
0
0
0
0

CA239
CA239A
CA25B
CA25BA
CA301A

LM239
LM239A
LM25B
LM25BA
LM301A

0
0
0
0
0

CA307
CA31 05
CA311
CA324
CA3290

LM307
LM675
LM311
LM324
LM393

0
S
0
0
S

CA339
CA339A
CA3401
CA35B
CA35BA

LM339
LM339A
LM3401
LM35B
LM35BA

0
0
0
0
0

CA741
CA747
CA74B
DG201
DG211

LM741
LM747
LM74B
LF13201
LF13201

0
0
0
0
0

DG212
HA·OP07
HA2400
HA2404
HA2405

LF13202
LM607
LM604
LM604
LM604

0
I

S
S
S

NSC
Part Number

Part Number

...n0

NSC
Part Number

til
til

HA2406
HA2420
HA2420
HA2500
HA2502

LM604
LH0023
LH0043
LM6161
LM6161

S
S
S
S
S

HA5141
HA5142
HA5144
HA5160
HA5160

LM4250
LF442
LF444
LF357
LH0062

S
0
0
S
S

HA2505
HA2510
HA251 0
HA251 0
HA2512

LM6361
LM11B
LM31B
LM6161
LM6161

S
S
S
S
S

HA5162
HA5170
HA5170
HA5170
HA5170

LH0062
LF151
LF155
LF156
LF157

S
S
S
S
S

HA2515
HA2520
HA2520
HA2522
HA2522

LM6361
LM6164
LM6113
LM6164
LM6113

S
S
S
S
S

HA5170
HA5170
HA51BO
HA51BO
HA51BO

LF355
LF356
LH0022
LH0042
LH0052

S
S
S
S
S

HA2525
HA2525
HA2529
HA2530
HA2535

LM6364
LM6313
LM6313
LH0024
LH0024

S
S
S
S
S

HF·10
HF·201
HF·300
HI·201
HI·50B

MF10
LF13201
AH5020
LF13201
LF1350B

0
0
S
0
S

HA2540
HA2541·2
HA2541·5
HA2542
HA2620

LH0032
LM6161
LM6361
LH0032
LH41 04

S
S
S
S
S

HI·509
HI·561B
HI·561B
HI·561B
HI·561B

LF13509
DACOBOO
DACOB06
DACOB07
DACOBOB

S
S
S
S
S

HA2620
HA2622
HA2625
HA2640
HA2640

LM6164
LM11B
LM31B
LHOO04
LM143

S
S
S
S
S

HI·565A
HI·5660
HI·56BO
HI·56B5
HI·56B5

DAC1265
DAC1266
DAC12BO
DAC1200
DAC12B5

0
0
S
S
S

HA2640
HA2645
HA2645
HA4741
HA5002

LM144
LM343
LM344
LM34B
LHOO02

S
S
S
S
S

HI·56B7
HI·56B7
HI·5690
HI·5695
HI·5697

DAC1201
DAC12B5
DAC12BO
DAC12B5
DAC12B5

S
S
S
S
S

HA5033
HA5020
HA51 02
HA5104
HA5135

LH0033
LM61B1
LMB33
LM837
LM637

S

HI·574
HI·574
HI·574
HI·574
HI·674

ADC10BO
ADC1210
ADC1211
ADC12BO
ADC10BO

S
S
S
S
S

I

S
S
S

The following notations are appended to assist you In finding the best option.
S = NSC Similar Device

I = NSC Improved Device

xxvii

D = NSC Direct Replacement

-...
:xl
CD
CD
CD
;:,

n

CD

~

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Z

C

3

CI"
CD

...

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CP

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Z

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CIS

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CP

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c

e

CP
CP

II:
U)
U)

0
~
(J

Part Number

NSC
Part Number

Part Number

HARRIS (GE/RCAllntersiI)
(Continued)

NSC
Part Number

Part Number

LINEAR TECHNOLOGY
CORP.

HI-674
ICH8530
ICL7114
ICL7114
ICL7660

ADC1280
LH0101
ADC1205
ADC1225
LMC7660

ICL8069
ICL8069
IH5009
IH5010
IH5011

LM313
LM385-1.2
AH5009
AH5010
AH5011

IH5012
IH6106
IH6206
LM741

AH5012
LF13508
LF13509
LM741

S
S
S
S
D

LF155
LF155A
LF156
LF156A
LF198

LF155
LF155A
LF156
LF156A
LF198

D
D
D
D
D

D
D
D
D
D

LF198A
LF355A
LF356A
LF398
LF398A

LF198A
LF355A
LF356A
LF398
LF398A

D
D
D
D
D

D
D
D
D

LF412A
LH0070
LH21 08
LH2108A
LM10

LF412A
LHOO70
LH2108
LH2108A
LM10

D
D
D
D
D

LM101A
LM107
LM108
LM108A
LM111

LM101A
LM107
LM108
LM108A
LM111

D
D
D
D
D

LM117
LM117HV
LM118
LM119
LM123

LM117
LM117HV
LM118
LM119
LM123

D
D
D
D
D

LM129
LM129A
LM134
LM136
LM137

LM129
LM129A
LM134
LM136
LM137

D
D
D
D

LM137HV
LM138
LM150
LM185
LM199

LM137HV
LM138
LM150
LM185
LM199

D
D
D
D
D

LM234
LM308A
LM311
LM317
LM317HV

LM234
LM308A
LM311
LM317
LM317HV

D
D

HITACHI

S

HA12012
HA12411
HA12412
HA12413
HA12417

LM833
LM3089
LM3189
LM1868
LM1863

HA13421A
HA1374
HA1389
HA1394
HA1397

LM18293
LM2877
LM384
LM2879
LM1875

HA17082
HA17082A
HA17084
HA17084A
HA17094

LF353
LF412
LF347
LF347B
LM2904

HA17301
HA17324
HA17339
HA17358
HA17393

LM3301
LM324
LM339
LM358
LM393

HA17458
HA17741
HA17747
HA17901
HA17902
HA17903

LM458
LM741
LM747
LM2901
LM2902
LM2903

D

S
S
S
S
S
S
S
S

D

D
D
D

LM318
LM319
LM323
LM329
LM329A

LM318
LM319
LM323
LM329
LM329A

D
D
D
D
D

LM334
LM336
LM337
LM337HV
LM338

LM334
LM336
LM337
LM337HV
LM338

D
D
D
D
D

LM350
LM385
LM399
LM399A
LT1001

LM350
LM385
LM399
LM399A
LH0044

D
D
D
D
D

LT1001
LT1003
LT1003
LT1003
LT1004

LM607
LM123
LM323
LM337
LM113

LT1004
LT1004
LT1005
LT1008
LT1008

LM185
LM385
LM2935
LM108
LM308

D
D

LT1009
LT1009
LT1010
LT1011
LT1012

LM136
LM336
LHOO02
LM311
LM312

D
D

LT1013
LT1014
LT1014
LT1019
LT1020

LM358
LM324
LM348
LM368
LP2951

D
D
D
D
S

LT1021
LT1022
LT1029
LT1031
LT1033

LM369
LF356
LM336
LH0070
LM133

The following notations are appended to assist you In finding the best option.
S

~

NSC Similar Device

I

~

NSC Improved Device

xxviii

D

~

NSC
Part Number

NSC Direct Replacement

I

S
S
D
D

S
D
D

S
D
D

D

D
D
D

.----------------------------------------------------------------------.0
Part Number

NSC
Part Number

Part Number

LINEAR TECHNOLOGY
CORP. (Continued)

NSC
Part Number

Part Number

a

=

NSC
Part Number

::D

;.

MAXIM

S

LT1033
LT1033
LT1034
LT1038C
LT1038M

LM137
LM333
LM385
LM396
LM196

LT1055
LT1056
LT111
LM317HV
LT117

LF355
LF356
LM111
LM317HV
LM117

D

LT118
LT119
LT123
LT123A
LT1223

LM118
LM119
LM123
LM123A
LM6181

D
D

LT137
LT150
LT1524
LT311
LT317

LM137
LM150
LM1524D
LM311
LM317

D
D
D

LT317A
LT318
LT319
LT323
LT323A

LM317A
LM318
LM319
LM323
LM323A

LT337
LT338
LT338A
LT350A
LT3524

LM337
LM338
LM338A
LM350A
LM3524D

LTC1059
LTC1060
LTC1099
REF·01
SG1524

MF5
MF10
ADC0820
LM368
LM1524D

SG3524

LM3524D

D
D

S
S

D
D
D

D

D
D

D

D
D
D
D
D
D

AD565
AD566
AD7523
AD7523
AD7523

DAC1265
DAC1266
DAC0830
DAC0831
DAC0832

D

AD7524
AD7524
AD7524
AD7533
AD7533

DAC0830
DAC0831
DAC0832
DAC1020
DAC1021

S
S
S
D
D

AD7533
AD7541
AD7541
AD7542
AD7542

DAC1022
DAC1218
DAC1219
DAC1208
DAC1209

AD7542
AD7545
AD7545
AD7545
AD7548
AD7548
AD7548
AD7820
ICL7642
MAX480

LM111
LM117
LM123
LM124
LM137

LM111
LM117
LM123
LM124
LM137

S
S
S
S

LM139
LM140
LM148
LM150
LM158

LM139
LM140
LM148
LM150
LM158

DAC1210
DAC1208
DAC1209
DAC1210
DAC1230

S
S
S
S
S

LM193
LM201
LM208
LM209
LM211

LM193
LM201
LM208
LM109
LM211

DAC1231
DAC1232
ADC0820
LMC6044
LMC6041

S
S

S
S

LM217
LM223
LM224
LM237
LM239

LM117
LM123
LM224
LM137
LM239

D
D
D
D
D

S
S
D

LM248
LM250
LM258
LM285
LM2900

LM248
LM150
LM258
LM285
LM2900

D
D
D
D

LM2901
LM2902
LM2903
LM2904
LM293

LM2901
LM2902
LM2903
LM2904
LM293

D
D
D
D
D

LM2931
LM301
LM307
LM308
LM309

LM2931
LM301
LM307
LM308
LM309

D
D
D
D
D

MOTOROLA

D
D
D
D

AD562
AD563
DAC·08
DAC·08
DAC·08

DAC1266
DAC1265
DAC0800
DAC0801
DAC0802

LF347
LF351
LF353
LF355
LF356

LF347
LF351
LF353
LF355
LF356

LF357
LF411
LF412
LF441
LF442

LF357
LF411
LF412
LF441
LF442

S

D

D

D

D

D
D

D
D
D

D
D

D
D
D

The following notations are appended to assist you In finding the best option.
S

~

NSC Similar Device

I

~

Cil
n

LF444
LM101
LM108
LM109
LM11

D

D
D
D

D

D
D
D

LF444
LM101
LM108
LM109
LM11

D
S
S
S

NSC Improved Device

xxix

D

~

NSC Direct Replacement

=

CD

~

D

"'U
III

D
D
D

c

D

D
D

D
D
D
D
D

D
D

D
D

D

::l.

z
3

C"

...
CD

~

CP
.CI

E
~

Z

1:

:.>.CI
CP

u
C

!

iia::
e
=

(,)

NSC
Part Number

NSC

Part Number

Part Number

NSC

Part Number

Part Number

Part Number

LM79MXX
LM320-XX
LM79XX
LM320-XX

I
I
D
I

/kA723
/k A741
/k A747
ADCOB03
ADCOB04

LM723
LM741
LM747
ADCOB03
ADCOB04

D
D
D
D
D

ADCOB05
ADCOB20
AM26L830
CA3089
DAC-OB

ADCOB05
ADCOB20
D83691
LM3089
DAC0801

D
D
D
D
D

DAC-OB
DAC-OB
ICM7555
LF198
LF224

DACOBOO
DAC0802
LMC555
LF198
LM224

D
D
D
D
D

LF298
LF398
LM111
LM119
LM124

LF29B
LF398
LM111
LM119
LM124

D
D
D
D
D

LM139
LM139A
LM158
LM193
LM193A

LM139
LM139A
LM15B
LM193
LM193A

D
D
D
D
D

LM211
LM219
LM224
LM239
LM239A

LM211
LM219
LM224
LM239
LM239A

D
D
D
D
D

LM258
LM2901
LM2903
LM293
LM293A

LM258
LM2901
LM2903
LM293
LM293A

D
D
D
D
D

MOTOROLA (Continued)
LM311
LM317
LM323
LM324
LM337

LM311
LM317
LM323
LM324
LM337

D
D
D
D
D

MC1596
MC1709
MC1710
MC1723
MC1741

LM1596
LM709
LM710
LM723
LM741

D
D
D
D
D

MC79MXXA
MC79XX
MC79XX
MC79XXA

LM339
LM340-XX
LM346
LM350
LM356

LM339
LM340-XX
LM34B
LM350
LM35B

D
D
D
D
D

MC1747
MC174B
MC3301
MC3302
MC3307B

LM747
LM74B
LM3301
LM3302
LMB33

D
D
D
D
8

PHILIPS

LM3B5
LM3900
LM393
LMB33
MC1391

LM3B5
LM3900
LM393
LMB33
LM1391

D
D
D
D
D

MC33079
MC3346
MC3346
MC3356
MC3356

LMB37
LM3046
LM3146
LM30B9
LM31B9

8
D
I
8
8

MC1408
MC140B
MC1408
MC1414
MC1436

DAC0806
DAC0807
DACOBOB
LM1414
LM343

D
D
D
D
I

MC3361
MC34001
MC34001
MC34001
MC34002

LM3361A
LF351
LF353
LF411
LF412

I
I

MC1437
MC14442
MC14444
MC145040
MC145041

LH2301
ADC0829
ADC0830
ADCOB11
ADC0811

8
8
8
8
D

MC34004
MC3401
MC3410
MC3412
MC3456

LF347
LM3401
DAC1020
DAC1265
LM556

I
D
D
8
D

MC1455
MC1456
MC1458
MC1468
MC1488

LM555
LM212
LM1458
LM325
D81488

D
8
D
8
D

MC35001
MC35002
MC3510
MC4741
MC7812

LF411
LF412
DAC1020
LM34B
LM7812

I
I
D
D
D

MC1489
MC1496
MC150B
MC1514
MC1536

D814B9
LM1496
DAC060B
LM1514
LM143

D
D
D
D
I

MC7B15
MC7824
MC7BLXX
MC78LXXA
MC78MXX

LM7815
LM7824
LM7BLXX
LM78LXXA
LM341-XX

D
D
D
D
D

MC1537
MC1537
MC1556
MC1558
MC1568

LH2101
LH2201
LM112
LM1558
LM125

8
8
8
D
8

MC7BMXX
MC78XX
MC78XXA
MC79LXX
MC79LXX

LM7BMXX
LM78XX
LM340A-XX
LM320L-XX
LM79LXXA

D
D
D
D
D

The fallowing natations are appended to aS81st you In finding the belt aptian.
S = NSC Similar Device

1= NSC Impravsd Device

xxx

D = NSC Direct Replacement

Part Number

NSC
Part Number

Part Number

NSC
Part Number

Part Number

...00

NSC
Part Number

(II
(II

::D

I

!1
CD
;

D

n

PHILIPS (Continued)
LM311
LM319
LM324
LM324A
LM339

LM311
LM319
LM324
LM324A
LM339

D
D
D
D
D

LM339A
LM358
LM393
LM393A
MC1408

LM339A
LM358
LM393
LM393A
DAC0807

D
D
D
D
D

MC1408
MC1458
MC1488
MC1488
MC1489

DAC0808
LM1458
D51488
D514C88
D51489

D
D
D

MC1489A
MC1489A
MC1496
MC1508
MC1596

D51489A
D514C89A
LM1496
DAC0808
LM1596

D

MC3302
MC3403
NE4558
NE5034
NE5118

LM3302
LM3403
LM833
ADC0841
DAC0830

D
D
5
5
5

NE5119
NE5410
NE5532
NE5532
NE555

DAC0830
DAC1020
LM833
LM833
LM555

NE556
NE565
NE566
NE567
5A532

LM556
LM565
LM566
LM567
LM2904

5A534
5E529
5E5537
5E555
5E556

LM2902
LM161
LF398
LM555
LM556

5E567
SG1532

LM567
LM1524

I
D

I
D
D
D

5

5
D
D
D
D
D
D
D

I
5
D
D
D

5G2524
5G3524

LM2524
LM3524

D
D

PRECISION
MONOLITHICS INC_
ADC-910
ADC-910
AMP-01
AMP01
BUF-03

ADC1025
ADC1061
LHOO38
LM363
LHOO33

5
5
5
5

BUF-03
CMP-08
CMP-08
DAC-02
DAC-02

LHOOO2
LM260
LM360
DAC1020
DAC1021

5
5
5
5
5

DAC-02
DAC-03
DAC-03
DAC-03
DAC-05

DAC1022
DAC1020
DAC1021
DAC1022
DAC1020

5
5
5
5
5

DAC-05
DAC-05
DAC-08
DAC-08
DAC-08

DAC1021
DAC1022
DAC0800
DAC0801
DAC0802

5
D
D
D

DAC-100
DAC-100
DAC-100
DAC-1408
DAC-1408

DAC1020
DAC1021
DAC1022
DAC0806
DAC0807

5
5
5
5
5

DAC-1408
DAC-312
DAC-888
DAC-888
DAC-888

DAC0808
DAC1266
DAC0830
DAC0831
DAC0832

5
D
5
5
5

MAT02
MAT02AH
MUX-08E
MUX-24E
OP-05

LM394
LM194H
LF13508
LF13509
LM607

5
5
D
D
5

I

5

OP-07
PP-07
OP-15
OP-215
OP-77

LM607
OP07
LF411
LF412
LM607

OP02
OP04
OP06
OP08
OP09

LM741
LM747
LM725
LM101
LM4136

5

OP11
OP11
OP14
OP14
OP14

LM324
LM348
LM1458
LM1558
LM358

5
5
5
5
5

OP15
OP15
OP15
OP160
OP177

LF351
LM301
LM310
LM6181
LM607

OP215
OP22
OP221
OP221
OP42

LF353
LM4250
LM2904
LM358
LHOO62

5
5
5
5
5

OP42
OP421
OP421
OP421
OP421

LM318
LM2902
LM324
LM3303
L2902

5
5
5
5
5

OP421
OP43
OP43GP
OP471
OP471

LP324
LM348
LF441ACN
LM149
LM837

5

OP490
OP77
OP97
PM0820
PM1008

LMC6044
LM607
LM311
ADC0820
LM308

5
5
5
D
D

D

The following notations are appended to assist you In finding the best option.
S

~

NSC Similar Device

I

~

NSC Improved Device

xxxi

D

~

NSC Direct Replacement

:::J

CD
C"

'<
5

"U
I»
~

5
5

3

5

5

5
5
5

5
5
5
5

Z

C

C"

...CD

.
II)

J:I

E

NSC
Part Number

::lI

Part Number

1:

PRECISION
MONOLITHICS INC.
(Continued)

Z

ca

II).

~
II)

u
C

!II)
Q)
IX
II)
II)

e

0

Part Number

NSC
Part Number

Part Number

REF-43
SMP10
SMP10
SMP11
SMP11

LM136
LF39B
LHOO43
LF39B
LHOO23

D
S
S
S
S

REF-01
REF-02
REF·02
REF·03

SSM2139
SSM2210
SW-06
SW-201
SW-202

LMB33
LM394
LF13333
LF13201
LF13202

S
S
D
D
D

SAMSUNG

PM1012
PM111
PM119
PM139
PM139A

LM312
LM111
LM119
LM139
LM139A

S
D
D
D
D

PM14B
PM155
PM155A
PM156
PM156A

LM14B
LF155
LF155A
LF156
LF156A

D
D
D
D
D

RAYTHEON

PM157
PM157A
PM20B
PM20BA
PM211

LF157
LF157A
LM20B
LM20BA
LM211

D
D
D
D
D

DAC-OB
DAC-10
DAC-10
DAC-6012
DAC-6012

DACOBOO
DAC-1020
DAC·1021
DAC-1220
DAC-1221

S
S
S
S
S

PM219
PM24B
PM30B
PM30BA
PM319

LM219
LM24B
LM30B
LM30BA
LM319

D
D
D
D
D

LH2101A
LH2111
LM101A
LM111
LM124

LH2101A
LH2111
LM101A
LM111
LM124

D
D
D
D
D

PM339A
PM355
PM355A
PM356
PM356A

LM339A
LF355
LF355A
LF356
LF356A

D
D
D
D
D

LM139
LM14B
LM2900
LM301A
LM324

LM139
LM14B
LM2900
LM301A
LM324

D
D
D
D
D

PM357
PM357A
PM725
PM741
PM747

LF357
LF357A
LM725
LM741
LM747

D
D
D
D
D

LM339
LM34B
LM3900
LP365
RC1458

LM339
LM34B
LM3900
LP365
LM1458

D
D
D
D
D

PM7533
PM7533
PM7533
PM7541
PM7541

DAC1020
DAC1021
DAC1022
DAC1218
DAC1219

D
D
D
S
S

RC1558
RC4156
RC4157
RC4195
RC4195

LM1558
LM348
LM348
LM325
LM326

D
S
S
S
S

REF-01
REF-01
REF-02
REF-03
REF-03

LM36B
LM369
LM368-5.0
LM336
LM385-2.5

S
S
S
S
S

RC714
RC741
RC747
REF-01
REF-01

LM607
LM741
LM747
LHOO70
LM368

I
D
D
S
S

LM369
LM336-5.0
LM36B-5
LM36B-5

I
S
S

KA219
KA2B03
KA2B07
KA301
KA319

LM219
LM1B51
LM1B51
LM301
LM319

D
S
S
D
D

KA331
KA3524
KA431
KA710
KA7BS40

LM331
LM3524D
LM431
LM710
LM7BS40

D
D
D
D
D

KF347
KF351
KF442
LM224A
LM239

LF347
LF351
LF442
LM224A
LM239

D
D
D
D
D

LM24B
LM25BA
LM2901
LM2902
LM2903

LM24B
LM25BA
LM2901
LM2902
LM2903

D
S
D
D
D

LM2904
LM293
LM311
LM324
LM324A

LM2904
LM293
LM311
LM324
LM324A

D
D
D
D
D

LM3302
LM339A
LM348
LM358A
LM393

LM3302
LM339A
LM348
LM358A
LM393

D
D
D
D
D

LM393A
LM741
MC1458
MC7BLXX
MC78MXX

LM393A
LM741
LM1458
LM78LXX
LM78MXX

D
D
D
D
D

The following notations are appended to a8818t you In finding the best option.
S

= NSC Similar Device

I

= NSC Improved Device

xxxii

D

NSC
Part Number

= NSC Direct Replacement

I

0

Part Number

NSC
Part Number

Part Number

NSC
Part Number

Part Number

a

NSC
Part Number

til
til

MC78XX
MC79MXX·
MC79XX
NE555
NE556

::tI
CD
CD

SAMSUMG (Continued)
LM78XX
LM79MXX
LM79XX
LM555
LM556

D
D
D
D
D

/L A741
/L A74B
L293
L4940
L4941

LM741
LM748
LM18293
LM2940
LM2940

D
D
D
5
5

L78MXX
L78505
L78XX
L78XX
L7912

LM78MXX
LM323
LM340-XX
LM78XX
LM7912

D

L79XX
L79XX
LF198
LF255
LF256

LM320-XX
LM79XX
LF198
LF255
LF256

D
D
D
D
D

LF257
LF29B
LF351
LF353
LF355

LF257
LF298
LF351
LF353
LF355

D
D
D
D
D

LF355A
LF356
LF356A
LF357
LF357A

LF355A
LF356
LF356A
LF357
LF357A

D
D
D
D
D

LF398
LM101A
LM109
LM117
LM123

LF398
LM101A
LM109
LM117
LM123

D
D
D
D
D

LM124
LM124A
LM134
LM135
LM137

LM124
LM124A
LM134
LM135
LM137

D
D
D
D
D

SGS THOMPSON

I
D
D
D

LM139
LM139A
LM148
LM158
LM158A

LM139
LM139A
LM148
LM158
LM158A

D
D
D
D
D

LM334
LM335
LM336
LM336B
LM339

LM334
LM335
LM336
LM336B
LM339

D
D
D
D
D

LM1837
LM193
LM193A
LM201A
LM20B

LM1837
LM193
LM193A
LM201A
LM20B

D
D
D
D
D

LM339A
LM346
LM348
LM358
LM358A

LM339A
LM346
LM348
LM358
LM358A

D
D
D
D
D

LM211
LM21B
LM219
LM223
LM224

LM211
LM21B
LM219
LM223
LM224

D
D
D
D
D

LM393
LM393A
NE555
NE556
5E555

LM393
LM393A
LM555
LM556
LM555

D
D
D
D
D

LM224A
LM234
LM235
LM236
LM239

LM224A
LM234
LM235
LM236
LM239

D
D
D
D
D

5G556
5G2524
5G3524
5G3525
5G3527

LM556
LM2524
LM3524
LM3525
LM3527

D
D
D
D
D

LM239A
LM246
LM248
LM258
LM2901

LM239A
LM246
LM249
LM258
LM2901

D
D
D
D
D

T5A2040
T5272
T5274
T527L2
T527L4

LM1875
LMC662
LMC660
LPC662
LPC660

5
5
5
5
5

LM2902
LM2903
LM2904
LM293
LM2930

LM2902
LM3903
LM2904
LM293
LM2930

D
D
D
D
D

T527M2
T527M4

LMC662
LMC660

5
5

LM2931A
LM301A
LM30B
LM308A
LM311

LM2931A
LM301A
LM308
LM30BA
LM311

D
D
D
D
D

!LA723
/L A741
/L A747
ADCOB01
ADC0802

LM723
LM741
LM747
ADC0801
ADCOB02

D
D
D
D
D

LM318
LM319
LM323
LM324
LM324A

LM318
LM319
LM323
LM324
LM324A

D
D
D
D
D

ADC0803
ADC0804
ADC0805
ADCOB20
CA30BeN

ADCOB03
ADC0804
ADCOB05
ADC0820
LM30Be

D
D
D
D
D

SIGNETICS

The following notations are appended to assist you In finding the best option.
S = NSC Similar Device
I = NSC Improved Device
D = NSC Direct Replacement

xxxiii

Cil

::J

n

CD
t:r

'<

"'U
I»

...
Z

c

3

t:r
CD

...

.
CP

.Q

E

NSC
Part Number

Z=

Part Number

1::

SIGNETICS (Continued)

~
CP

.

()

C
CP
CP
CP

a:
0
0

2
(.)

NSC
Part Number

Part Number

NSC
Part Number

SILICONIX

CIS

Do

Part Number

DAC-08
DAC-08
DAC-08
ICM7555
LF198

DAC0800
DAC0801
DAC0802
LMC555
LF198

0
0
0
0
0

DG201
DG202
DG211
DG212
DG508

LF13201
LF13202
LF13201
LF13202
LF13508

0
0
0
0
0

LM158
LM185
LM193
LM201
LM207

LM158
LM185
LM193
LM201
LM207

0
0
0
0
0

LF298
LF398
LM2901
LM2903
LM311

LF298
LF398
LM2901
LM2903
LM311

0
0
0
0
0

DG509

LF13509

0

LM211
LM217
LM218
LM224
LM237

LM211
LM217
LM218
LM224
LM137

0
0
0
0
0

LM319
LM324
LM339
LM358
LM393

LM319
LM324
LM339
LM358
LM393

0
0
0
0
0

LM239
LM248
LM258
LM2900
LM2901

LM239
LM248
LM258
LM2900
LM2901

0
0
0
0
0

MC1408
MC1458
MC1496
NE5034
NE5118

DAC0807
LM1458
LM1496
ADC0841
DAC0830

0
0
0

LM2902
LM2903
LM2904
LM2907
LM2917

LM2902
LM2903
LM2904
LM2907
LM2917

0
0
0
0
0

NE529
NE532
NE541 0
NE5517
NE5537

LM361
LM358
DAC1020
LM13600
LF398

S

LM293
LM2930
LM2931
LM301
LM307

LM293
LM2930
LM2931
LM301
LM307

0
0
0
0
0

NE555
NE565
NE566
NE567
SA532

LM555
LM565
LM566
LM567
LM2904

0
0

LM317
LM318
LM324
LM330
LM337

LM317
LM318
LM324
LM330
LM337

0
0
0
0
0

SA534
SE5118
SE529
SE532
SE5410

LM2902
DAC0830
LM161
LM158
DAC1020

I
S
S
S
S

LM339
LM348
LM358
LM385
LM3900

LM339
LM348
LM358
LM385
LM3900

0
0
0
0
0

SE566
SE567
SG3524

LM566
LM567
LM3524

0
0
0

LM393
LP111
LP211
LP239
LP2901

LM393
LP311
LP311
LP339
LP339

S
S
S
S

S
S

0
S

0
0

D

0

TEXAS INSTRUMENTS
UA2240
pA709
p.A723
p.A741
p.A747

LM2240
LM709
LM723
LM741
LM747

0
0
0
0
0

p.A748
p.A78LXX
p.A78MXX
fJ-A78XX
p.A79MXX

LM748
LM78LXX
LM78MXX
LM78XX
LM79MXX

0
0
0
0
0

p.A79XX
ADC0803
ADC0804
ADC0805
ADC0808

LM79XX
ADC0803
ADC0804
ADC0805
ADC0808

0
0
0
0
0

ADC0809
ADC0820
ADC0831
ADC0832
ADC0834

ADC0809
ADC0820
ADC0831
ADC0832
ADC0834

0
0
0
0
0

ADC0838
LF198
LF347
LF351
LF353

ADC0838
LF198
LF347
LF351
LF353

0
0
0
0
0

LF398
LF411
LF412
LM101A
LM107

LF398
LF411
LF412
LM101A
LM107

0
0
0
0
0

LM108
LM111
LM124
LM139
LM148

LM108
LM111
LM124
LM139
LM148

0
0
0
0
0

The following notations are appended to assist you In finding the best option.
S

~

NSC Similar Device

I

~

NSC Improved Device

xxxiv

D

~

NSC Direct Replacement

0

Part Number

NSC
Part Number

Part Number

TEXAS INSTRUMENTS
(Continued)
LP311
LP339
LT1004
LT1009
MC1458

LP311
LP339
LM385
LM336
LM1458

D
D
D
D
D

NSC
Part Number

Part Number

TLC14
TLC1541
TLC20
TLC252
TLC254

MF4-100
ADC1031
MF10
LMC662
LMC660

D
S
D
S
S

LMC662
LMC662
LMC660
LMC6042
LMC6044

S
S
S
I
I
I
S
S

MC155
MC3303
MC3403
MC79LXX
MF10

LM1558
LM3303
LM3403
LM79LXX
MF10

D
D
D
D
D

TLC25L2
TLC25M2
TLC25M4
TLC27L2
TLC27L4

MF4
NE555
NE555
NE592
OP07

MF4
LM555
LM556
LM592
OP07

D
D
D
D
D

TLC27L7
TLC27M2
TLC27M4
TLC271
TLC272

LMC6062A
LMC662
LMC660
LMC6041
LMC6032

OP27
OP37
RC4136
RC4558
SA555

LM627
LM63
LM4136
LM833
LM555

I
I

TLC274
TLC277
TLC339
TLC532
TLC533

LMC6034
LMC6082A
LP339
ADC0829
ADC0829

I
S
S
D

SA556
SE2524
SE3524
SE555
SE556

LM556
LM2524D
LM3524D
LM555
LM556

D

TLC540
TLC541
TLC545
TLC546
TLC549

ADC0811
ADC0811
ADC0819
ADC0819
ADC0831

S
D
S
D
S

SE592
TL061
TL062
TL064
TL071

LM592
LF441
LF442
LF444
LF351

D

TLC555

LMC555

D

LF411
LF353
LF412
LF347
ADC0808

I
I
I
I
D

LM1391
LM386
LM1877
LM2896
LM2877

S

TL071
TL072
TL072A
TL074
TL0808

TA7133
TA7140
TA7230
TA7232
TA7233

TL0809
TL081
TL082
TL084
TL087

ADC0809
TL081
TL082
LF347
LF411

D
D
D
I

TA7268
TA7269
TA7282
TA7283
TA7313

LM1875
LM2878
LM2896
LM2896
LM386

S
S
S
S
S

TL088
TL287
TL288
TL317
TL431

LF411
LF412
LF412
LM317
LM431

S
S
D
D

TA7336
TA7366
TA7367
TA7370
TA7504

LM390
LM3914
LM3914
LM3361
LM741

S
S
S
S
D

TL592
TLC04
TLC0820
TLC10
TLC1225

LM592
MF4
ADC0820
MF10
ADC1225

D
D
D
D
D

TA75061
TA75062
TA75064
TA75071
TA75072

LF441
LF442
LF444
LF351
LF353

D
D
D

I
I
D
D

I
I
I
I

S
S

TOSHIBA
S

S
S
S

~

NSC Similar Device

I

~

NSC Improved Device

XXXV

D

~

NSC
Part Number

(II
(II

LF347
LM2902
LM324
LM2901
LM339

I
S
D
D

TA75358
TA75358
TA75393
TA75393
TA75458

LM2904
LM358
LM2903
LM393
LM1558

I
D
I
D
D

TA7555
TA7612
TA7613
TA7630
TA7640

LM555
LM3914
LM1868
LM1036
LM1868

D
S
S
S
S

TA76524
TA7654
TA7667
TA7688
TA7758

LM3624
LM3914
LM3915
LM1896
LM1868

S
S
S
S
S

TA7769
TA78LXX
TA78MXX
TA78XXX
TA79LXXX

LM1896
LM78LXX
LM78MXX
LM78XX
LM79LXX

S
D
D
D
D

TA79XXX
TA8117
TA8119
TA8202
TA8211

LM79XX
LM1868
LM1896
LM1877
LM2878

D
S
S
S
S

TC9154

LMC1982

S

L293
UC117
UC137
UC150
UC1524

LM18293
LM117
LM137
LM150
LM1524D

D
D
D
D

UC2524
UC317
UC337
UC350
UC3524

LM2524D
LM317
LM337
LM350
LM3524D

D
D
D

UC78XX
UC78XX
UC79XX
UC79XX

LM340-XX
LM78XX
LM320-XX
LM79XX

D
D
D
D

UNITRODE

NSC Direct Replacement

:0

TA75074
TA75092
TA75092
TA75339
TA75339

The following notations are appended to assist you In finding the best option.
S

...00
CD
CD

n;

::I

n

CD

-i
"U

I»

;::a.
Z

c

3

D"
CD

...

~

Industry Package Cross-Reference Guide

NSC

CJ

mm

~=

~
In

@

CJ
~

D

m

/LA

Signetics

Motorola

TI

AMD

Spraque

0

R

4/16 Lead
Glass/Metal DIP

0

D

I

L

Glass/Metal
Flat Pack

F

F

Q

F

F,
S

F

G

L

H

U

J

0

H

P

A,
B,
M

T,
TO-99, TO-100, TO-5

H

B-, 14- and 16-Lead
Low Temperature
Ceramic DIP

J

~

0

NSC

H

R,
D

K,
L,
DB

F

(Steel)
K
TO-3

KS

KC

K

DA

N

T,
P

N,

K

K

(Aluminum)

B-, 14- and 16-Lead
Plastic DIP

'With

dual~n-line

formed leads

"With radically formed leads

xxxvi

V

P

P,

N

NSC

~~

~~
t
~
~~~

NSC
/LA

Signetics

Motorola

TI

AMD

Sprague

.:c!

"U

I»

n

:II;"

TO-202
(D-40, Durawatt)

I»

P

CO
CD

...

(')

oen
~

:::u

TO-220
3-&5-Lead
TO-220
11-, 15- & 23-Lead

T

U

U

;.

KC

Ci1

:s

T

g
Ci)

c

a:
CD
Low Temperature
Glass Hermetic
Flat Pack

W

F

TO-92
(Plastic)

Z

W

M

5

5

F

W

F

P

LP

D

D

L

DW

LW

G

0

lCiitUUJ

RRRRRRRRRR

50

(Narrow Body)
(Wide Body)

WM

D
•
1::1 1::1 1::1 1::1 1::1

5'
a.
c
!!

I:U:I 1::11::1 1::1

bUUUUUiR:RJd

xxxvii

5,
D

CD

:5!
~

NSC

CJ
CD
u

NSC

/LA

Signetics

Motorola

TI

AMD

Spraque

c

e

CD
CD

a::•

e=

0

PCC

V

Q

A

FN

FN

L

EP

LCC
Leadless Ceramic
ChlpCarrler

E

L1

G

U

FKI
FG/FH

L

EK

CD

Q

.=
til

Go

~

1S
~

'a

.5

~

II~~~~~~~II

xxxviii

Section 1
Linear Voltage
Regulators

•

Section 1 Contents
Linear Voltage Regulators Definition ofTerms . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Linear Voltage Regulators Selection Guide ............................................
LM104/LM204/LM304 Negative Regulators.......................... .. ...... .........
LM105/LM205/LM305/LM305A1LM376 Voltage Regulators............. ... .... ... .....
LM109/LM309 5-Volt Regulators.....................................................
LM117/LM117A1LM317/LM317A 3-Terminal Adjustable Regulators..... .. ... ... . ... .. ...
LM117HVILM317HV 3-Terminal Adjustable Regulators . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM120/LM320 Series 3-Terminal Negative Regulators... .... .......... ......... ..... ...
LM123A1LM123/LM323A1LM323 3-Amp, 5-Volt Positive Regulators............ ...... ...
LM125/LM325/LM325A, LM126/LM326 Voltage Regulators.... ............ ..... .... ...
LM133/LM333 3-Amp Adjustable Negative Voltage Regulators................... ..... ...
LM137/LM337 3-Terminal Adjustable Negative Regulators..............................
LM137HVILM337HV 3-Terminal Adjustable Negative Regulators (High Voltage) . . . . . . . . . . . .
LM138/LM338 5-Amp Adjustable Regulators ..........................................
LM140AlLM140/LM340AlLM340/LM7800/LM7800C Series 3-Terminal Positive
Regulators. .................... ... .... . ...... ......... ........ ... .. .......... ...
LM140L/LM340L Series 3-Terminal Positive Regulators..................... ............
LM145/LM345 Negative 3-Amp Regulators.... ....... ..................... ............
LM150/LM350/LM350A 3-Amp Adjustable Power Regulators...... .. .... .............. ..
LM196/LM396 10-Amp Adjustable Voltage Regulators. .. ......... .......... . .... ..... ..
LM317L 3-Terminal Adjustable Regulator.... ... ....... .. .............. .............. ..
LM320L, LM79LXXAC Series 3-Terminal Negative Regulators............................
LM337L 3-Terminal Adjustable Regulator...... .... ............................ .. ... ...
LM341 I LM78MXX Series 3-Terminal Positive Regulators . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM342 Series 3-Terminal Positive Regulator....... ..... ...... ...... ... .... . ......... ..
LM431A Adjustable Precision Zener Shunt Regulator... .. ............... ....... .. ... ...
LM723/LM723C Voltage Regulators.. ... .. ........... ....... ... ....... ...... ... ... ...
LM78G 4-Terminal Adjustable Regulator..............................................
LM78LXX Series 3-Terminal Positive Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM78MG 4-Terminal Adjustable Voltage Regulator. .. ......... ......... ...... ..........
LM79MXX Terminal Negative Regulators . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM79XX Series 3-Terminal Negative Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

1-2

1-3
1-4
1-8
1-12
1-19
1-25
1-37
1-47
1-56
1-62
1-70
1-77
1-83
1-89
1-101
1-112
1-116
1-120
1-132
1-144
1-155
1-159
1-161
1-170
1-175
1-182
1-191
1-197
1-207
1-213
1-220

~National

~ Semiconductor

Voltage Regulators
Definition of Terms
Current-Limit Sense Voltage: The voltage across the current limit terminals required to cause the regulator to current-limit with a short circuited output. This voltage is used
to determine the value of the external current-limit resistor
when external booster transistors are used.

Output-Input Voltage Differential: The voltage difference
between the unregulated input voltage and the regulated
output voltage for which the regulator will operate within
specifications.
Output Noise Voltage: The RMS ac voltage at the output
with constant load and no input ripple, measured over a
specified frequency range.

Dropout Voltage: The input-output voltage differential at
which the circuit ceases to regulate against further reductions in input voltage.

Output Voltage Range: The range of regulated output voltages over which the specifications apply.

Feedback Sense Voltage: The voltage, referred to ground,
on the feedback terminal of the regulator while it is operating in regulation.

Output Voltage Scale Factor: The output voltage obtained
for a unit value of resistance between the adjustmentterminal and ground.

Input Voltage Range: The range of dc input voltages over
which the regulator will operate within specifications.

Quiescent Current: That part of input current to the regulator that is not delivered to the load.

Line Regulation: The change in output voltage for a
change in the input voltage. The measurement is made under conditions of low dissipation or by using pulse techniques such that the average chip temperature is not significantly affected.

Ripple Rejection: The line regulation for ac input signals at
or above a given frequency with a specified value of bypass
capacitor on the reference bypass terminal.

Load Regulation: The change in output voltage for a
change in load current at constant chip temperature.

Standby Current Drain: That part of the operating current
of the regulator which does not contribute to the load current. (See Quiescent Current)

Long Term Stability: Output voltage stability under accelerated life-test conditions at 12S'C with maximum rated voltages and power dissipation for 1000 hours.

Temperature Stability: The percentage change in output
voltage for a thermal variation from room temperature to
either temperature extreme.

Maximum Power Dissipation: The maximum total device
dissipation for which the regulator will operate within specifications.

Thermal Regulation: Percentage change in output voltage
for a given change in power dissipation over a specified time
period.

1-3

_National
Semiconductor
Linear Voltage Regulators Selection Guide
Adjustable Positive Voltage Regulators
Output
Current
(A)

10.0
5.0
3.0

1.5

1.0
0.5 .

0.1

Device

Output
Voltage

Input
Voltage
(V)'

(V)

LM350

1.2 to 32

LM350A

1.2 to 32

LM117

1.2 to 37

LM117A

1.2 to 37

LM117HV

1.2 to 57

LM317

1.2 to 37

LM317A

1.2 to 37

LM317HV

1.2 to 57

s: 20
s: 20
Diff. s: 40
Diff. s: 40
Diff. s: 35
Diff. s: 35
Diff. s: 35
Diff. s: 40
Diff. s: 40
Diff. s: 60
Diff. s: 40
Diff. s: 40
Diff. s: 60

LM78GC

5to 30

7.5 to 40

LM196

1.25t015

LM396

1.25to 15

LM138

1.2 to 32

LM338

1.2t032

LM150

1.2 to 32

Page
No.

Diff.

- 55'C to

K2

1-132

O'C to

K2

1-132

K2

1-89

LM117

1.2 to 37

Dill.

1.2 to 37

Diff.

LM117HV

1.2 to 57

Dill.

LM317

1.2t037

Dill.

LM317M

1.2 to 37

Diff.

LM317A

1.2 to 37

Dill.

LM317AM

1.2 to 37

Diff.

LM317HV

1.2 to 57

Diff.

LM78MGC

5t030
1.2 to 37

+ 150'C
+ 125'C
- 55'C to + 150'C
O'C to + 125'C
- 55'C to + 150'C
O'C to + 125'C
-40'Cto + 125'C
- 55'C to + 150'C
-55'Cto + 150'C
- 55'C to + 150'C
O'C to + 125'C
-40'Cto + 125'C
O'C to + 125'C
O'C to + 150'C
- 55'C to + 150'C
- 55'C to + 150'C
-55'Cto + 150'C
O'C to + 125'C
O'C to + 125'C
-40'Cto + 125'C
-40'C to + 125'C
O'C to + 125'C
O'C to + 150'C
-40'C to + 125'C

Package
Availability"

Diff.

LM117A

LM317L

Operating
Temperature
(TJ)

s: 40
s: 40
s: 60
s: 40
s: 40
s: 40
s: 40
s: 60

7.5 to 40
Diff.

s: 40

K2,T3

1-89

K2

1-120

K2,T3

1-120

K2,T3

1-120

K2

1-25

K2···

1-25

K2

1-37

K2,T3

1-25

K2. T3

1-25

K2,T3

1-37

P4

1-191

H3, E20'"

1-25

H3'"

1-25

H3

1-37

H3

1-25

P3

1-25

H3

1-25

P3

1-25

H3

1-37

P4

1-207

M8,Z3

1-25

*In cases where the regulator is "floating" the maximum input-ta-output voltage differential is listed.
"Under Package Availability the letter identifies the type of package available and the number indicates the number of leads of the indicated package.
For example: T5 ~ 5·Lead TO·220, and Me ~ II-Lead Surface Mount.
E: Leadless Ceramic Chip Carrier
H: Metal Can (TO·39, TO-99)
K: Metal Can (T0-3)
M: Small Outline Molded Package (Surface Mount)
P: TO·202
T: TO·220
Z: TO·92

"'''''''Available in indicated package only as a military specified device.

1-4

c:
....m

;:,

Adjustable Negative Voltage Regulators
Output
Current
(A)

3.0
1.5

0.5

0.1

Output
Voltage
(V)

Input
Voltage
(V)'

Operating
Temperature
(TJ)

LM133

-1.210 -32

Dill. ,;; 35

-55'Clo + 150'C

K2

1-70

LM333

-1.210 -32

Dill. ,;; 35

-40'Clo + 125'C

K2, T3

1-70

:lI

LM137

-1.210 -37

Dill. ,;; 40

-55'C 10 + 150'C

K2

1-77

CQ

LM137A

-1.210 -37

Dill.';; 40

-55'C 10 + 150'C

K2'"

1-77

LM137HV

-1.210 -47

Ditl.,;; 50

-55'C 10 + 150'C

K2

1-83

LM337

-1.210 -37

Dill. ,;; 40

O'Clo + 125'C

K2,T3

1-77

LM337HV

-1.210-47

Dill. ,;; 50

O'C 10 + 125'C

-1.210 -37

Dill. ,;; 40

-55'C 10 + 150'C

K2
H3

1-83

LM137
LM137A

-1.210 -37

Dill. ,;; 40

-55'Clo + 150'C

H3'"

1-77

LM137HV

-1.210 -47

Dill. ,;; 50

-55'Clo + 150'C

H3

1-83

LM337

-1.210 -37

Dill. ,;; 40

O'C 10 + 125'C

H3

1-77

LM337M

-1.210 -37

Dill. ,;; 40

O'Clo +125'C

P3

1-77

LM337HV

-1.210 -47

Dill. ,;; 50

O'C 10 + 125'C

LM337L

-1.210 -37

Dill.';; 40

-25'C 10 + 125'C

Device

Package
Availability"

Page
No.

1-77

H3

1-83

M8,Z3

1-77

~

=
III

CQ

CD
CD

c
iii

8'
~

en
CD

Cii

ao·
;:,

C)

c
is:
CD

Building Block Adjustable
Positive and Negative Voltage Regulators
Output
Cu(rent
(mA)

150
45

Output
Voltage
(V)

Input
Voltage
(V)

Operating
Temperature
(TJ)

LM723

21037

9.51040

-55'C 10 + 150'C

LM723C

21037

9.51040

O'Clo + 150'C

LM105

4.51040

8.51050

-55'Clo + 150'C

LM205

4.51040

8.51050

LM305

4.51040

8.51050

LM305A

4.51040

Package
Availability"

Page
No.

Hl0, J14, E20'"

1-182

Hl0, J14, M14, N14
H8

1-182
1-12

-25'Clo +100'C

H8

1-12

O'Clo +85'C

H8

1-12

8.51050

O'C 10 + 150'C

H8

1-12

91040
-810 -50

O'C 10 + 100'C

N8

1-12

LM104

51037
-0.01510 -40

-55'Clo + 150'C

Hl0

1-8

LM204

-0.01510 -40

-810 -50

-25'Clo + 125'C

Hl0

1-8

LM304

-0.03510 -30

-810 -40

O'C to + 100'C

Hl0

1-8

Device

LM376
25

'In cases where the regulator Is "floating" the maximum Input·to·output voltage differential Is listed.
"Under Package Availability the letter Identifies the type of package available and the number Indicates the number of leads of the Indicated package.
For example: T5 = 5·Lead TO·220, and MB = B·Lead Su~ace Mount.
E: Leadless Ceramic Chip Carrier
H: Metal Can (TO·39. TO·99, TO-100)
J: Ceramic Dual·ln·Llne Package
K: Metal Can (TO·3)
M: Small Outline Molded Package (Su~ace Mount)
N: Molded Dual-ln·Llne Package
P: TO·202
T: TO·220
Z: TO·92
'''Available In Indicated package only as a military specified device.

1-5

•

(II

'a

'5

Fixed Positive Voltage Regulators

c

Output
Current
(A)

CJ

Output
Voltage

Max Input

(V)

(V)

LM123

5

20

LM123A
LM323
LM323A

5
5

20
20

5

20

- 55'C to + 150'C
O'C to + 125'C
-40'C to + 125'C

LM140
LM140A

5,12.15
5,12,15

35
35

- 55'C to

E

LM340
LM340A

...ca

LM78XX
LM78XXC

5,12,15
5,12,15
5,8,12,15,18,24

35
35
35

5,6,8,12,15,18,24

35
35

o

~

'i)

en

3.0

i

'3
c:n
(II
a:

1.5

(II

;g
(II

c
:::i

1.0
0.5

Device

LM109
LM309
LM140
LM140A
LM341

0.1

5
5,6,8,12,15,24
15
5,12,15
5,6,8,12,15

35
35
35
35

LM109

24
5

35
40
35

LM309

5

35

LM342

5
12,15

30
35
35

LM78MXXC
0.2

5

Voltage

LM140LA
LM340LA
LM78LXXAC

5,12,15
5,12,15
5,12,15
5, 6.2, 8.2, 9, 12, 15

35
35
35

Operating
Temperature

(TJ)
-55'C to + 150'C

+ 150'C
+ 150'C
O'C to + 150'C
O'C to + 150'C
- 55'C to + 150'C
O'C to + 150'C
- 55'C to + 150'C
O'C to + 125'C
- 55'C to + 150'C
- 55'C to + 150'C
- 40'C to + 125'C
- 40'C to + 125'C
-40'Cto + 125'C
- 55'C to + 150'C
O'C to + 125'C
O'C to + 150'C
O'C to + 150'C
-55'C to + 150'C
O'C to + 150'C
O'C to + 125'C
O'C to + 125'C
- 55'C to

Package
Availability'

K2
K2
K2
K2
K2
K2
K2,T3
K2,T3
K2
K2,T3
K2
K2
H3"
H3*'

Page
No.

1·56
1·56
1·56
1·56
1·101
1·101
1·101
1·101
HOI
1·101
1·19
1·19

P3, T3

1·161

H3,T3

1·161
1·161
1·19

T3
H3
H3
P3

H9
1·170

P3
H3
H3,Z3

1·170
1·112
1·112

H3,M8

1·197
1·197

Z3

'Under Package Availability the letter identifies the type of package available and the number indicates the number of leads of the indicated package.
For example: T5 = 5-Lead TO-220, and M8 = 8-Lead Surface Mount
H: Metal Can (T0-39)
K: Metal Can (TO-3)
M: Small Outline Molded Package (Surface Mount)
P: TO-202
T: TO-220
Z: TO-92
.. Available in indicated package only as a military specified device. The specHications for the LM140H and LM140AH are not contained in the LMI40 datasheet. If
specifications for these devices are required. contact your locel National Semiconductor sales office or authorized Distributor. For the pin-out of the LM140H
and LM140AH look to the LM140 datasheet.

1·6

Fixed Negative Voltage Regulators
Output
Current
(A)
3.0
1.5

Output
Voltage
(V)

Min Input
Voltage
(V)

LM145

-5, -5.2

-20

- 55'C to

K2

1-116

LM345

-5, -5.2

-20

O'C to

K2

1-116

-5

-25

K2

1-47

-12, -15

-35

K2

1-47

-5

-25

K2, T3

1-47

-12, -15

-35

-5

-35

Device

LM120
LM320
LM79XXC

0.5

-8, -12, -15

-40

LM120

-5

-25

LM320

-5

-25

-5

-25

-12, -15

-35

-5

-25

LM320M

-8

-30

-12, -15

-35

LM120

-12, -15

-35

LM320

-12, -15

-35

LM320L

-5, -12, -15

-35

LM79LXXAC

-5, -12, -15

-35

LM79MXXC
0.2
0.1

Operating
Temperature
(TJ)

+ 150'C
+ 125'C
- 55'C to + 150'C
-55'C to + 150'C
O'C to + 125'C
O'C to + 125'C
O'C to + 125'C
O'C to + 125'C
- 55'C to + 150'C
O'Cto + 125'C
O'C to + 125'C
O'C to + 125'C
O'C to + 125'C
O'Cto + 125'C
O'C to + 125'C
-55'C to + 150'C
O'Cto + 125'C
O'C to + 125'C
O'C to + 125'C

Package
Availability'

Page
No.

K2, T3

1-47

K2,T3

1-220

K2,T3

1-220

H3

1-47

H3

1-47

P3

1-47

P3

1-47

H3, P3, T3

1-213

H3, T3

1-213

H3, P3, T3

1-213

H3

1-47

H3

1-47

Z3

1-155

M8,Z3

1-155

Shunt Voltage Regulators
Output
Current
(A)
0.15

Device

Output
Voltage
(V)

Max Input
Voltage
(V)

Operating
Temperature
(TJ)

LM431AI

2.5 to 36

37

-40'Cto

LM431AC

2.5 to 36

37

O'C to

+ 150'C
+ 150'C

Package
Availability'
Z3

1-175

M8,Z3

1-175

'Under Package Availability the leller identifies the type of package available and the numbar indicates the number of leads of the indicated package.
For example: TS = S-Lead TO-220. and MS = S·Lead Surface Mount.
H: Metal Can (T0-39)
K: Metal Can (TO-3)
M: Small Outline Molded Package (Surface Mount)
P: TO-202
T: TO-220
Z: TO·92

1·7

Page
No.

~

:i ~ National
~ ~ Semiconductor
~

:i~ LM 104/LM204/LM304 Negative Regulator
....o
:i General Description
The LM104 series are precision voltage regulators which
can be programmed by a single external resistor to supply
any voltage from 40V down to zero while operating from a
single unregulated supply. They can also provide O.Ol-percent regulation in circuits using a separate, floating bias
supply, where the output voltage is limited only by the
breakdown of external pass transistors. Although designed
primarily as linear, series regulators, the circuits can be used
as switching regulators, current regulators or in a number of
other control applications. Typical performance characteristics are:
• Subsurface zener reference
• 1 mV regulation no load to full load
• 0.Q1 %IV line regulation
• 0.2 mVIV ripple rejection
• 0.3% temperature stability over military temperature
range

The LM104 series is the complement of the LM105 positive
regulator, intended for systems requiring regulated negative
voltages which have a common ground with the unregulated
supply. By themselves, they can deliver output currents to
25 mA, but external transistors can be added to get any
desired current. The output voltage is set by external resistors, and either constant or fold back current limiting is made
available.
The LM104 is specified for operation over the -55°e to
+ 125°e military temperature range. The LM204 is specified
for operation over the - 25°e to + 85°e temperature range.
The LM304 is specified for operation from ooe to + 7OCC.

Schematic Diagram
ADJUSTMENT
1

9
R17

1.5K

019....

..OIl

17~~

01

~
>-.
..

rC

017
09
M012

RI
2.3K

~05

... 022
016

01
010....

--

~

RI
10K

020

Cl
5 pF

~015

~

... 023

RIO
3K

fH-

RI
UK

lOOSTER
.-1. OUTPUT

jo'

.'"

C2~

R3
7K

R13
lK

-J021

RS
UK

~06
2
REFERENCE

J

---

D~~
6.3V

04
R2
7.8K

J

REGULATED
~ OUTPUT

...013

O~

RIS
15K

R14
2K

07

R4
14K

GROUND

Rl&
15K

6 CURRENT
LIMIT
~

024

Rll
10K

5 UNREGULATED
INPUT

15pFT

4
COMPENSATION

3
REFERENCE
SUPPLY

TL/HI77S4-1

1-8

Absolute Maximum Ratings
If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
(Note 6)
LM104/LM204
50V
50V
500mW

Input Voltage
Input-Output Voltage Differential
Power Dissipation (Note 1)
Operating Temperature Range
LM104
LM204
LM304
Storage Temperature Range
Lead Temperature (Soldering, 10 sec.)

LM304
40V
40V
500mW

ris:
.....
o
~
ris:
N
o
~
ris:
Co)
o
~

-55'C to + 125'C
- 25'C to + 85'C
O'Cto +70'C
- 65'C to + 150'C
300'C for hermetic

-65'C to + 150'C
260'C for plastic

Electrical Characteristics
Parameter

LM104/LM204

Conditions
Min

Typ

LM304

Max

Min

Typ

Units
Max

Input Voltage Range

-50

-8

-40

-8

Output Voltage Range

-40

-0.Q15

-30

-0.035

V

2.0
0.5

50
50

2.0
0.5

40
40

V
V

V

Output-Input Voltage
Differential (Note 3)

10 = 20 rnA
10=5mA

Load Regulation (Note 4)

0,,; 10"; 20 rnA
Rsc = 150

1

5

1

5

mV

Line Regulation (Note 5)

VOUT"; -5V
AVIN = 0.1 VIN

0.056

0.1

0.056

0.1

%

0.2
0.5

0,.5
1.0

0.2
0.5

0.5
1.0

mVIV
mVIV

2.0

2.2

2.0

2.2

V/kO

0.3

1.0

0.3

1.0

%

Ripple Rejection

C19 = 10 fLF, f = 120 Hz
VIN < -15V
-7V ~ VIN ~ -15V

Output Voltage Scale Factor

R2-3 = 2.4k

Temperature Stability

Vo"; -1V

Output Noise Voltage

10Hz,,;f,,; 10kHz
Vo ,,; -5V, Cl.9 = 0
Cl.9 = 10 fLF

Standby Current Drain

1.8

0.007
15

IL = 5 rnA, Vo = 0
Vo = -30V
Vo = -40V

1.8

0.007
15

1.7

2.5

3.6

5.0

1.7
3.6

%
fLY

2.5
5.0

rnA
rnA
rnA

Vo"; -1V
Long Term Stability
0.01
1.0
0.01
1.0
%
Nole 1: The maximum junction temperature of the LM104 is ISO"C, while that of the LM204 is 12S'C and LM304 is 100"C. For operating at elevated temperatures,
devices in the Hl0C rackage must be derated based on a thermal resistance of IS0'C/W, junction to ambient, or 4S'C/W, junction to case.
Nole 2: These specifications apply for junction temperatures between -SS'C and IS0'C (between -25"C and 100"C for the LM204 and O'C to +8S'C for the
LM304) and for input and output voltages within the ranges given, unless otherwise specified. The load and line regulation specifications are for constant junction
temperature. Temperature drift effects must be taken into account separately when the unit is operating under conditions of high dissipation.
Note 3: When external booster transistors are used, the minimum output·input voltage differential is increased, in the worst case, by approximately 1V.

Nole 4: The output currents given, as well as the load regulation, can be increased by the addition of external transistors. The improvement factor will be roughly
equal to the composite current gain of the added transistors.

Nole 5: With zero output, the de line regulation is determined from the ripple rejection. Hence,
determined from the ripple rejection, must be added to find the worst-case line regulation.
Nole 6: Refer to RETS104X drawing for military specifications for the LM104.

1-9

with output voltages between OV and - SV, a de output variation,

•

Typical Performance Characteristics
Load Regulation

Load Regulation

l

I I I

.
~.

j

-I

-3

!;

-&

o

..
~

-.... 110..
-2

...~

,

...

~

-10

o

10

...
~

.
..
.~
co

,

,

~ 0.02

::
~

c 0JJ4

~

~
>

I'

>

0,02

2D
3D
4D
DC INPUT VOLTAGE (V)

10

Current Limit Sense Voltage
D.I
D.8

~

•~

2D

>

!;

-10

-

OJ

o

3D

40

a

&0

ID

2D

3D

50

40

DC INPUT VOLTAGE (V)

Minimum Input Voltage
•.0

'lII"~

-"

I-' -

"

10

-75

0 15 511 75 100 12& 1&0

Line Transient Response

~

0.4

'"

-

....

Va~T"IOV

...

nc,,-o

t,SS",
CoUT -, pF

i

.\ I

"'/
II

VOUT -'BV
20

f\
\

t,SSm

.
... .....

Standby Current Drain

•

VI~'-&~

-

I
II

~

...

-75 -50 -25 0 2& SO 75 100 IZ& 1&0
JUNCTION TEMPERATURE ('CI

CauT'1 ~FINL-&mA..._
In- 15mA

CD

§:

I!:

La

0 25 5D 7& 1110 121 ISO
JUNCTION TEMI'ERATURE I"C)

41

~

IL. C,.· D.o, pF

.!!-:&:~I--+-I-

-so -2&

Load Transient Response

~

4V1N-IV

-20

t::; po

~

i-""

"""

~
I I

......

JUNCTION TEMPERATURE I"C)

ID

~

J

I-

~!!;

!-~au~=I~V

......

OA

.
.C
..~
.. .....

0.•

C,.-IU"F

/

-75 -&0 -25

i..

I

f-120H.

./

D.5

40

I

0.1

I-~"'O

D.I

5

&D

V!"'~'llv •.~.

.=.
=
~

BI D.7

~
co

4a

Ripple Rejection

Regulator Dropout Voltage
12

I,D

§:

~

3D

DC INPUT VOL TAGE (V)

~

c

Va.--IV

'"

50

10

i

i\

0.01

i

-!'-

o

za

LOAD CURRENT (mAl

\

'"

~

..

10

I,a

~
!!!

\

O,H

cl

o

3D

O,U

0,01

o

I

Supply Voltage Rejection With
Preregulated Reference Supply

Supply Voltage Rejection

I

R C',Bn

LOAD CURRENT {mAl

0,1

~

20

t::t-

i

lffl - i--

.:'

~ ''-- ~

LOAD CURRENT (..A)

I

I"

. -"'5.

ll.:' ! -

-I

&10112011

~

I......
Roc' 25Sl

I

- -.,.~ 1_1~- :~ ItL -_:L
:t
,

~ t-..

-4
-&

I

10

c

~

l

-4

I!:

~

-

~

Roc .lln

>

..

~.~~

I

-2

.~

i..
;

~I
~.~
Ie ~-..i ~.~"c

Current Umlting

~

......
~

.... ~ :-

I!:

10

TIME"")

2D

3D

a
10

TlME{",)

20

3D

o

10

20

30

40

OUTPUTVDLTAGf (VI
TL/H/7754-7

1-10

Connection Diagram
Metal Can Package
NC

REG

REF

OUTPUT

REF

BOOSTER

SUPPl Y

UNREG
INPUT

TL/H/7754-2
Note: Pin 5 connected to case.

Top View
Order Number LM104H, LM204H or LM304H
See NS Package H10C

Typical Applications
Operating with Separate Bias Supply

Basic Regulator Circuit

r-------t-~--------_t----GNO

r---------~~--~~--~-------GND

CIt
4.1 ~F

-r------------~--------~--t_---Vour·~
} -....- - - - - - Vour •

~

' - - - - - - - - - - t _ - - - -...- - - - - - - V,.
TlIH/7754-5

tSolid Tantalum
tSolid Tantalum

Trim RI for exact scale factor.

TLlH/7754-3

High Current Regulator

Switching Regulator

r------.----~--------_t------GNO

}---....--_t------

r-----~----.-----~--_.-------GND

Vour • -IOV
lOUT -

Note 1: The maximum junction temperature of the LM 105 and LM305A is 150"C, the LM205 and LM376 is 1aooe, and the LM305 is 8SoC. For operation at elevated temperatures, devices in the HOSG package must be derated based
on a thermal resistance of 168°C/W junction to ambient, or 25°C/W junction to case. For the epoxy dual-in-line package, derating is based on a thermal resistance of 138°C/W junction to ambient. Peak dissipations to 1W are
allowable providing the dissipation rating is not exceeded with the power average over a five second interval for the LM105 and LM205, and averaged over a two second interval for the LM305.
Note 2: Unless otherwise specified, these specifications apply for temperatures within the operating temperature range, for input and output voltages within the range given, and for a divider impedance seen by the feedback terminal
of 2 kfi. Load and line regulation specifications are for a constant junction temperature. Temperature drift effects must be taken into account separately when the unit is operating under conditions of high dissipation.
Note 3: The output currents given, as well as the load regulation, can be increased by the addition of external transistors. The improvement factor will be roughly equal to the composite current gain of the added transistors.
Note 4: With no external pass transistor.

Note 5: Refer to RETS105X Drawing for military specifications for the LM105.

,

-

Typical Performance Characteristics lM105/lM205/lM305/lM305A
Load Regulation

•.
.... .....

is

"""l !:II:. ~

z

:i
~
~

...

-001

~

-0.01

~

·OOl

·0.04

.....

I
T,=15DC

.~

.

',"-55'1:

I
I
1D

•
~

.

"

lOAD CURRENT ImAI

•

......

....

,....
......

-, 5

50

25

D

Z5

~UNCTION

.

50

75

IDa 125 ISO

I
-0.1 D

.

•

1D

..

3D

LOAD CURAENT ImAI

.

-15 -511

-25

.....

i'.

....,."

,....

r-..

""-I...

25 SO

"

-15

"
,.

rei

~~~~~~~.,~~-+~~
~~~r--~~~~~+-~~

~-LLL,L._~_,L,_~-L~"

OUTPUT VOLTAGE IVI

Supply Voltage Rejection

r-T--r-.-r--i-~~-,

"

You, = lOY

...

~
~

ODS

E

0.02

~

Vou,"OV
T....

2~oC

1'-'.... ,

0.01

~

~ ooos

50

15

100

125

i

1~'!::5-_-::":-C_'!::5-:.--:,1:-,-:':
..:-:,1:-,-::,,,:-:'.,,,

./

,~

0002
000'

1/

,.

..• ~~
IDO 125

.-

0··'0

~

12S·C

I-"~

"

3D
..
INPUT VOLTAGE (VI

"

Transient Response
Rsc ·'U1
.6V, ... ·sv

LINE

, iOUT=I'DV

~ -"
~

"..... .....,..

~.

.

oS
z
a

zs·c

~-

0
2!1 50 75
TEMPERATURE ,0Cl

."

-S~C

,..

20

INPUT OUTPUT VOLTAGE DIffERENTIAL IV)

Standby Current Drain

1.1

r-- r:'i2:~:';1
10

TEMPERATURE (!CI

/

-so -n

24

15 100 US 150

"

,.

~

Regulator Dropout Voltage

i"

..

3D

u H+'kl-r---t-~--t-1H

=:

......

AMBIENT TEMPERATURE

Minimum Output Voltage

"

al Rsc -tOn

i""" i"-o ~ ~

... • ..n

TEMPERATURE (oCI

.

~

H.-IOU

AIC-nn

R.=100

2S

'4~~~HH~~~~~~

Optimum Divider Resistance
Values

I
0

~-

>

RIlfRz·:r,n

I'

"

-7-

OUTPUT CURRENT ImAI

r-+--r-+-r-+--r-+~

i.-"

-~

HI~ .~

J.~-rrtr-~-·~'r··'~'~'VT'~"'~~

.....

-75-50-250

"

---::~--::

-

J'rT-rrrr----~--,

•
•

Minimum Input Voltage

"

'0

Short Circuit Current

TEMPERATURE eel

r-- V~UT ~'.5~

"r,~~~I~~t-~~~~

~

',"2ft

3D

I"

'.1

....

-"."

~

..........

"IC"'OO

.

T,·-SS-C

.

ro~5mA

,

~~

-.oo

Current Limit Sense Voltage
0

. .
.
",2*
•

~~

~ -0.02

...

I

L
I I

•

-

~-IT",~ ~

I

Current Limiting
Characteristics

Load Regulation

.

_ R sc ·'00

-CL"O

'uO

I

_-_C:L~11£f

In' ZDII'IA
: - - INL =I.0mA
VOUT= IOV

,.,.-

JLDlD

-400

10

TlMEI.lS)

"

3D

TUH/7755-6

1-15

Typical Performance Characteristics LM376
Load Regulation

..

l

,, ,,

co

~
...i!:

Q.3

~

Q.2

>

0.1

co

....

Current Limiting Characteristics

~J

0.4

Rsc '0

co

T.-W'

l\

II!!-~-

:,...

~Sr

...

"co

1.00

~

T. =0

"
I!:

~

III

T.·25',

~

>
....
~

11.10

.~

'0
21
LOAD CURRENT (mAl

~
>

U

....

&.I
a.7

II!"

30

!::;
~

I

1.350

I

:::;

I:

~

15
20
25
OUTPUT CURRENT (mAl

I"""

iii

B

.251
.2ao

30

Zi
&0
70
AMBIENTTEMPERATURE rei

VQUT-l0V
ILII

11.9

-

~

!: 11.7

i

ZDnlA

.UI

Ci

~

1""' ....
~

VOl

...

1'0

IL·l0mA/I!

B.B

11.&

8.&

IIA HILj&j/l

10
70
AMIIENTTEMPERATURE rCI
25

Standby Current Drain
TA = 2S'C

I

2.B
2.7
2.B

A

II

Supply Voltage Rejection

Vo"1.72X(:; +~

1\

Z.5

ZA

"'\'1r'

2.3
Z.2

L
1.0,&20Z53031
OUTPUT VOLTAGE (VI

,

40 Transient Response

2.00

~o.D3o

1.9&
C '.10
.! 1.11

i

1.10

;

1.1&

I; 1.70
1.85
I;; 1.81
1.61
1.60

!

i

o.D3l

Vo· ,av

a
~

21
ZI 31 31
INPUTVDLTADE (VI

-

~R.,-I,an

..

.o.VIN -IV
VOUT 'IOV

Roc' lin

,

.... e,·hF

,

!::

r···

50.010
40

LINE'

-CL-Q

0.011

~io' ~:::"r·il~
11

1\

.. o.OZO

A'1"'T
..J,...fo-

.0

VouT -1OV

T.· ZI'C
I,;'ZOH.
CRI!'-.

1.'J2xA,

z v;:T.7I

2..
2.0

11.3
21
50
70
AMBIENT TEMPERATURE rei

A,· 1.11 Vg IUl

2.1

Rsc-·1In

~ 11.'

i-""

Optimum Divider Resistance
3.D

lZ.3
12.2
12.1
~ 12.0

i

i.o"

......

~ .3111

I
10

1.,;5mA

~A811

Regulator Dropout Voltage

VOUT= IV

,

...

I
I

I

Minimum Input Voltage

co

Rsc -111n
I

us

Current Limiting Sense Voltage

~

I!

- r:

!::

.

7.3
7.2
~ 7.'
7.0

T.-71r'- ;T.·H'C
T.-IrC

0.75

"co

~

,, ,,

I ,

11
.1
20
21
3D
INPUT·DUTPUTVOLTADE DIFFERENTIAL (VI

....

1,1.· II RIA
INt.- 1.OmA
VOUT'10V

LOAD

I
II

I

I
za

3D

TIME"'~

TL/H17765-7

1·16

Typical Applications
10A Regulator with Foldback Current Limiting
r - -.........--1~--...........J.>I'V'Io--1~------1~...--VOUT

C3t

+
3.3~FI

R3

15V

R4

1 10V

Rl

47

03
2N3172

~ 5V

Cl·
500~F

0.16

R5
6.6

5.55K
1%

C4t
4.7~Fl

TL/H/7755-4

1.0A Regulator with Protective Diodes
021
UTR3305

r---I1II.....- - - <....-

. .- - - - -.........--1~..-

Your ~ 26V

R3
0.2

011
Rl

UTR3305

31K
1%

tProtects against shorted input or inductive leads on

R2
2.13K

----1

1%

VIN _ ..._ _....__

unregulated supply.
·Protects against input voltage reversal.

:j:Protects against output voltage reversal.

C3
I~F

35V

TLlH17755-5

Linear Regulator with Foldback Current Limiting

Current Regulator

, - - - - - - - - - - - - - -....- - - t - - - r--...-"Iw- lBV ...

1.8
2W

R3

lOUT

510

=

lA

TL/H/7755-8
TL/H/7755-9

1-17

Typical Applications (Continued)
Shunt Regulator

.,

IN3821
3.3V

"'

IUK

(i}_~-+_--+'%

"'

U4K
1%

L-~----------~----------4----4-~roDJ~
TL/H/7755-10

..

Switching Regulator

Basic Positive Regulator with Current Limiting
Pc

2M

~~-""-VDUT"'1.72 R1~R2

r+'-...,..---.....-----i--"t-....-1r-- Vour - IV
DI

V

v"

UTXIII

4JpF

325

Isc'"' -

"sc

VJN> 8.5V

"2

tSolid tantaium.

:~K

*,25 turns ~22 on Amold
Engineering A262123-2
motybdenum perm ally

mA

TL/H17755-12

core. TLlH/7755-11

1.0A Regulator with Protective Diodes
Dlt
UT"33G5

Dlt

UT"3305

tProtects against shorted
input or inductive loads on
unregulated supply.

VIN-"-~~----i

'Protects against input
voltage reversal.

C3

I.'
35V

*Protects against output
voltage reversal.

TL/H/7755-13

Linear Regulator with Foldback Current Limiting
R4
8

r--~I---JV~---~------~--_~_~mF;'~

"5
43

VIN> lav
"3
510

TL/H17755-14

1·18

r-------------------------------------------------------------'r
3:
....
o

~National

~
r
3:
Co)

~ Semiconductor

~

LM109/LM309 5-Volt Regulator
General Description
The LM109 series are complete 5V regulators fabricated on
a single silicon chip. They are designed for local regulation
on digital logic cards, eliminating the distribution problems
association with single-point regulation. The devices are
available in two standard transistor packages. In the solidkovar TO-5 header, it can deliver output currents in excess
of 200 mA, if adequate heat sinking is provided. With the
TO-3 power package, the available output current is greater
than lA.
The regulators are essentially blowout proof. Current limiting
is included to limit the peak output current to a safe value. In
addition, thermal shutdown is provided to keep the IC from
overheating. If internal dissipation becomes too great, the
regulator will shut down to prevent excessive heating.
Considerable effort was expended to make these devices
easy to use and to minimize the number of external components. It is not necessary to bypass the output, although this
does improve transient response somewhat. Input bypassing is needed, however, if the regulator is located very

far from the filter capacitor of the power supply. Stability is
also achieved by methods that provide very good rejection
of load or line transients as are usually seen with TTL logic.
Although designed primarily as a fixed-voltage regulator, the
output of the LM109 series can be set to voltages above 5V,
as shown. It is also possible to use the circuits as the control element in precision regulators, taking advantage of the
good current-handling capability and the thermal overload
protection.

Features
• Specified to be compatible, worst case, with TTL and
DTL
• Output current in excess of 1A
• Internal thermal overload protection
• No external components required

Schematic Diagram
r-----.---------~----_1--------~--.__INPUT

OJ
6.JV

RIJ
2K

RI4
O.J

•

zr----------_1--+-----1--------1--0UTPUT

4n

04
6.JV

DIll
R4

UK
~--+---~--~---4--~--~~--4_--4__GROUNO

TUHI713B-l

1-19

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 3)
Input Voltage
35V
Power Dissipation
Internally Limited

Operating Junction Temperature Range
- 55·C to
LM109
LM309
O·C to
- 65·C to
Storage Temperature Range
Lead Temperature (Soldeiing, 10 sec.)

+ 150·C
+ 125'C
+ 150·C
300·C

Electrical Characteristics (Note 1)
Parameter

LM109

Conditions

=

Output Voltage

Tj

Line Regulation

TJ = 25'C
7.10V ,,; VIN ,,; 25V

Load Regulation
TO·39 Package
TO·3 Package

Tj = 25'C
5 rnA ,,; lOUT"; 0.5A
5 rnA,,; lOUT"; 1.5A

Output Voltage

7.40V ,,; VIN ,,; 25V,
5 rnA ,,; lOUT"; IMAX'
P < PMAX

Quiescent Current

7.40V ,,; VIN ,,; 25V

Quiescent Current Change

7.40V ,,; VIN ,,; 25V
5 rnA ,,; lOUT"; IMAX

Output Noise Voltage

TA = 25·C
10Hz"; f,,; 100kHz

25'C

LM309

Typ

Max

Min

Typ

Max

4.7

5.05

5.3

4.8

5.05

5.2

V

4.0

50

4.0

50

mV

15
15

50
100

15
15

50
100

mV
mV

5.25

V

10

rnA

0.5
0.8

rnA
rnA

4.6

5.4

5.2

4.75

10

5.2

0.5
0.8
40

Long Term Stability

10

Ripple Rejection

Tj = 25·C

Units

Min

50

40

p.V

20

mV

50

dB

Thermal Resistance,
(Note 2)
Junction to Case
·C/W
TO·39 Package
15
15
·C/W
TO·3 Package
2.5
2.5
Note I: Unless otherwise specified. these specifications apply - SS"C ,;; TJ ,;; + ISO"C for the LMI09 and O"C ,;; TJ ,;; + 125"C for the LM309; VIN = 10V; and
lOUT = O.IA for the T0-39 package or JOUT = O.SA for the TO·3 package. For the T0-39 package,lMAJ( = 0.2A and PMAX = 2.0W. For the TO-3 package,lMAX
= I.OA and PMAX = 20W.
Note 2: Without a heat sink, the thermal resistance of the TO·39 package is about 150"C/W, while that of the TO·3 package is approximately 3S"C/W. WRh a heat
sink, the effective thermal resistance can only approach the values specified, depending on the effiCiency of the sink.
Note 3: Refer to RETSI09H drawing for LMI09H or RETSI09K drawing for LMI09K military specifications.

Connection Diagrams
Metal Can Packages
G~D

DUTPUTA~(CASEI

.~"
Z

•

INPUT

3

I

£c)

GND
(CASEI

•

~

TLlHI713B-3
Order Number LM109K STEEL or LM309K STEEL
See NS Package Number K02A

Order Number LM109H or LM309H
See NS Package Number H03A

For Aluminum Package
Order Number LM309K
See NS Package Number KC02A

1·20

r-----------------------------------------------------------------------------,
Application Hints
a. Bypass the Input of the LMI 09 to ground with., 0.2 /LF
ceramic or solid tantalum capacitor if main filter capacitor
is more than 4 inches away.
b. Use steel package instead of aluminum if more than
5,000 thermal cycles are expected. (.6.T ., 50'C)
c. Avoid Insertion of regulator Into "live" socket if input
voltage is greater than 10V. The output will rise to within
2V of the unregulated input if the ground pin does not
make contact, possibly damaging the load. The LM109
may also be damaged if a large output capacitor is
charged up, then discharged through the internal clamp
zener when the ground pin makes contact.
d. The output clamp zener is designed to absorb transients only. It will not clamp the output effectively if a
failure occurs in the internal power transistor structure.
Zener dynamic impedance is :::: 40. Continuous RMS
current into the zener should not exceed 0.5A.
e. Paralleling of LM109s for higher output current is not
recommended. Current sharing will be almost nonexistent, leading to a current limit mode operation for devices
with the highest Initial output voltage. The current limit
devices may also heat up to the thermal shutdown point
(:::: 175'C). Long term reliability cannot be guaranteed
under these conditions.

f. Preventing latchoff for loads connected to negative
voltage:

......

If the output of the LM109 is pulled negative by a high current supply so that the output pin is more than 0.5V negative
with respect to the ground pin, the LM109 can latch off. This
can be prevented by clamping the ground pin to the output
pin with a germanium or Schottky diode as shown. A silicon
diode (1 N4001) at the output is also needed to keep the
positive output from being pulled too far negative. The 100
resistor will raise + VOUT by :::: 0.05V.

g

I+VIN

LMIDB

.........--r--~t--+VOUT
02

IN4DDI

: C O M - - _ t - - -...- t

. . . . .-----t...

--VOUT
TLlHI713B-7

Crowbar Overvoltage Protection
Input Crowbar

Output Crowbar

+VIN

.......-

...-

...--+VOUT

TL/HI713B-B

TL/H/713B-9

'Zener Is Internal to LMI09.
"Ql must be able to withstand 7A continuous current if fusing is not used at regulator Input. LM109 bond wires will fuse at currents above 7A.
tC2 is selected for surge capability. Consideration must be given to filter capacitor size, transformer impedance, and fuse blowing time.
ttTrip point is:::: 7.5V.

1-21

r

...gs:::

!!:

Typical Performance Characteristics
Maximum Average
Power Dissipation (LM109K)

Maximum Average
Power Dissipation (LM309K)
Z4

.
i

I
i

25
AIIIBIENrrEMPERATURE rc)

50

15

.00

.25

.1t3
10

100

1k

I.

lOOk

1M

FREQUENCY (HI)

AMBIE.TTEMPERATURE ('C)

TLlH/713B-l0

Maximum Average
Power Dissipation (LM109H)

Maximum Average
Power Dissipation (LM309H)

2.4 r--r-....,.......,.-r--r---r-r-""1

INFINITE

TO·39

HEAT SINK

Ripple Rejection

•

VIN=~DV

•

I
.r .....M5mA

'0

~

0

I

0

z0
.0

0~L-~~~~--L-~·

0

25

50

15

.-:;;:;V

•••••J

0

i

-aD -25

I

~

z

"

LlVIN"'3VplI
i··Z5'C

.00 125 .50

.00

.k

AMBIENT TEMPERATURE ('C)

AMBIENTTEMPERATURE rC)

.Ok

IL':'\
J ,M
'OOk

FREQUENCY (Hd

TLlHI713B-11

Current Limit
Characteristics (Note 1)

Thermally Induced Output
Voltage Variation

Ripple Rejection
90

3~-r--r--r--r--r-'

.-

V

"

..................

..

•3
"

~=a:

CII

B

V,N"OV
Ti'25"C

0.51-+-1-+--+-1-+-1-1

"'fHI
60

D

0.5

1.D

OUTPUT CURRENT (AI

TL/HI713B-12

Note 1: Current limiting foldback characteristics
are determined by input output differential, not by output voltage.

1·22

Typical Performance Characteristics
Input-Output Differential (V)

Output Voltage (V)

2.5

e:

i

~

2.D
•.5

;;;

5
~

i

'- ILJ'A
.~:--.
IL""ZOmA

••0

IL"'IA
5.850

~

Tj'r5'C

I/"

~ 5.025

tB=: !

....... :::::

Output Voltage (V)
5.25

5.015

-::::

",:, :--. ......

(Continued)

e:w

IL=5mA

~ 5.05

5.DDO

.......

1/

>

Tj=-5S·C

>-

~ 4.95

~

IL j2DOrA

VIN,·DV

r-

~

Ti=15lrC
4.975

5.15

S 4.950

D.5

4.85
4.925

lVOU{"'IDOmr
D
-15 -f0 -26 D 25 50 15 .DD .25 15D
JUNCTION TEMPERATURE rCI

I

4.!JDD&

8

1

4.1~75 -60 -25 D 25 5D 15 10D 126 16D

9

INPUT VOLTAGE (VI

JUNCTION TEMPERATURE C'CI

TLlHI7.3B-.3

Quiescent Current

Quiescent Current

5.3

<

.!
>- 5.1
ill

~
~

!:i

4.8

Output Voltage Noise

5.'
~

5.3

<

.s

!;;

i

~

Tj--5S"C

.

5 4.9

Tj-'5D'C

4.8
4.1

4.!1& -fD -25 D 25 5D 15 .00 125 150
JUNCTION TEMPERATURE C'CI

i

5.1

/~
5

.0

--

2.
3D
20
INPUT VOLTAGE IVI

!

~

.D III

~

0.1=

.~

~

~

"

W

4D

35

15

IDO

....

.3
>

5.0

'1~

~
...,.

~

~

a

'L"~~~

~

A ~

5.2

I.D

10-

Tj=2S"C

VIN"'lDV
.......
'L~O
'\
.......
/"-

:./

..

I

IUD
lak
FREQUEfICY/DArIDl'llDTH CHz!

10

I
.allk

TLlH1713B-14

Line Transient Response

Load Transient Response

~!

15

;;
E

~g

~;
.. >

=w

....

i~.

IL=tA

a

...
UIL- SmA

~{

a •• -

-10

:?

.

>-"

~i
E~

I

2

3 4
TIME '"'I

f\

II

0

9~4DD

0.5
D

In

.. <

4VIN-1V

0

VIN -Iav
f-CL=D.1",F

Tj'25'C

SCi_200

IL ...

;; U

!!Se

-

>;::

5

~~

!::!:i

~z 200

Tj"25'C

~~ -5

gg

....

1Uf-~L·O.I"F

5

200

D

tr-""' lOOns

0

I

2

3 4
TlME("sJ

5

6

TLiH/713B-IS

1-23

•

Typical Applications
Fixed 5V Regulator

Adjustable Output Regulator

....._ ._ _ OUTPUT

INPuT--4..........

INPUT--4~...:.f

~v

t-=--4"'- OUTPUT
BV' VOUT <2.BV

Cl*
1.Dp.F
SOLlD
TANTALUM

Cl
O.22,.F

C2 ~ l.D,&F t
SOLID
TANTALUM

-

TLlH17138-4
TLlH17138-2

'Required If regulator Is located more than 4' lrom power supply Illter capacitor.
tAlthough no output capacitor Is needed lor stability, It does Improve tran·
slent response.
C2 should be used whenever long wires are used to connect to the load, or
when transient response Is critical.
Note: Pin 3 electrically connected to case.

High Stability Regulator·

OUTPUT

'-.....,r.:-......f---------~f_-------------------~~--1~
SlA
R2
6K

.Doall

R4t
510

0.211

+ e3 1
10~F

01
IN829
&.2V

RI
30K

'Regulation better than 0.01 %, load, line and temperature, can be obtained.
tDetermlnes zener currenl May be adjusted to minimize thermal drift.
*Solid tantalum.

TL/H17138-5

Current Regulator
IN'UT--t~...:.t

RI*
'----.--OUTPUT
TL/H17138-6

'Determines output current. If wirewound resistor is used, bypass with 0.1 ,.F.

1-24

r-------------------------------------------------------------------------,~

........
~
3:
....
....

3:

~National

~ Semiconductor

~

LM117A/LM117/LM317A/LM317
3-Terminal Adjustable Regulator

::!

General Description

....

The LM117 series of adjustable 3-terminal positive voltage
regulators is capable of supplying in excess of 1.5A over a
1.2V to 37V output range. They are exceptionally easy to
use and require only two external resistors to set the output
voltage. Further, both line and load regulation are better
than standard fixed regulators. Also, the LM117 is packaged
in standard transistor packages which are easily mounted
and handled.

the adjustment terminal to ground which programs the output to 1.2V where most loads draw little current.
For applications requiring greater output current, see LM150
series (3A) and LM138 series (5A) data sheets. For the negative complement, see LM137 series data sheet.

Besides replacing fixed regulators, the LM117 is useful in a
wide variety of other applications. Since the regulator is
"floating" and sees only the input-to-output differential voltage, supplies of several hundred volts can be regulated as
long as the maximum input to output differential is not exceeded, i.e., avoid short-circuiting the output.
Also, it makes an especially simple adjustable switching regulator, a programmable output regulator, or by connecting a
fixed resistor between the adjustment pin and output, the
LM117 can be used as a precision current regulator. Supplies with electronic shutdown can be achieved by clamping

Part Number
Suffix

Package

Rated
Power
Dissipation

K
H

TO-3

20W

1.5A

TO-39

2W

0.5A

T

TO-220

20W

1.5A

MP

TO-202

2W

0.5A

E

LCC

2W

0.5A

Digitally Selected Outputs

LM117

lMI17

I
I
V1N------I1vIN ADJVOUTIt----+-VOUT
~ Rl
•

240

_ _ Cl*

~"

~""R2

•• R2*

5k

~

••

TLlH/9063-1
Full output current not available at high input-output voltages
*Needed if device is more than 6 inches from filter capacitors.
tOptional-improves transient response. Output capacitors In the range of
1 "F to 1000 "F of aluminum or tantalum electrolytic are commonly used
to provide improved output impedance and rejection of transients.
ttVOUT

....
.......

Features
• Guaranteed 1 % output voltage tolerance
(LM117A, LM317A)
• Guaranteed max. 0.Q1 %N line regulation
(LM117A, LM317A)
• Guaranteed max. 0.3% load regulation
(LM117A, LM117)
• Guaranteed 1.5A output current
• Adjustable output down to 1.2V
• Current limit constant with temperature
• P+ Product Enhancement tested
• 80 dB ripple rejection
• Output is short-circuit protected

1.2V-2SV Adjustable Regulator

/.

~

3:
Co)

Design
Load
Current

Typical Applications

--O.I~F

~
......

LM117 Series Packages and Power Capability

In addition to higher performance than fixed regulators, the
LM117 series offers full overload protection available only in
IC's. Included on the chip are current limit, thermal overload
protection and safe area protection. All overload protection
circuitry remains fully functional even if the adjustment terminal is disconnected.
Normally, no capacitors are needed unless the device is
situated more than 6 inches from the input filter capacitors
in which case an input bypass is needed. An optional output
capacitor can be added to improve transient response. The
adjustment terminal can be bypassed to achieve very high
ripple rejection ratios which are difficult to achieve with standard 3-terminal regulators.

~

3:
Co)

= 1.2SV ( 1 + ~) + IADJ(R2l

''-----.-~, *
INPUTS

TL/H/9063-2

·Sets maximum VOUT

1-25

•

,....
.,...
C")

:E
....I

......
~
.,...
C")

::E
....I

r::.,....,...
::E
....I

~.,....,...

::E
....I

Absolute Maximum Ratings (Note 1)

Operating Temperature Range

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 2)
Power Dissipation

O'C,:;; TJ ,:;; +125'C

Preconditioning

+40V, -0.3V

Storage Temperature

-55'C,:;; TJ':;; +150'C
-40'C':;; TJ':;; +125'C

LM317

Internally Limited

Input-Output Voltage Differential

LM117A1LM117
LM317A

Thermal Limit Burn-In

All Devices 1000/0

- 65'C to + 150'C

Lead Temperature
Metal Package (Soldering, 10 seconds)
Plastic Package (Soldering, 4 seconds)

300'C
260'C

ESD Tolerance (Note 5)

3 kV

Electrical Characteristics
Specifications with standard type face are for TJ = 25'C, and those with boldface type apply over full Operating Temperature Range. Unless otherwise specified, VIN - VOUT = 5V, and lOUT = 10 mAo (Note 3)
LM117A (Note 2)

Conditions

Parameter
Reference Voltage

3V ,:;; (VIN - VOUT) ,:;; 40V,
10 mA ,:;; lOUT':;; IMAX' P ,:;; PMAX
Line Regulation

Load Regulation

Thermal Regulation

Typ

Max

1.238

1.250

1.262

1.225

1.250

1.270

3V ,:;; (VIN - VOUT) ,:;; 40V (Note 4)

10 mA ,:;; lOUT':;; IMAX (Note 4)

20 msPulse

Adjustment Pin Current

O/ON
O/ON
0/0

0.1

0.3

0.1

0.3

0.3

1

0.3

1

0/0

0.03

0.07

0.03

0.07

O/O/W

50

100

50

100

p.A

0.2

5

0.2

5

p.A

3.5

5

3.5

5

mA

3.4
1.8

1.5
0.5

2.2
0.8

3.4
1.8

A
A

0.3
0.15

0.4
0.2

A
A

0.003

0.003

0/0

85

85

dB

80

dB

1.5
0.5

2.2
0.8

(VIN - VOUT) = 40V
KPackage
H, K Packages

0.3
0.15

0.4
0.2

VOUT = 10V, f
CADJ = 10 p.F

=

120 Hz,

=

1

68

V

0.02

(VIN - VOUT) ,:;; 15V
K Package
H, K Packages

120 Hz,

1.30

0.05

Current Limit

=

1.25
0.01

(VIN - VOUT)

VOUT = 10V, f
CADJ = 0 p.F

1.20

0.02

TMIN ,:;; TJ ,:;; TMAX

Ripple Rejection Ratio

V

0.01

Minimum Load Current

10Hz':;; f,:;; 10kHz

Units

Max

0.02

Temperature Stability

40V

Typ

0.005

10 mA,:;; lOUT':;; IMAX
3V ,:;; (VIN - VOUT) ,:;; 40V

RMSOutput Noise, % of VOUT

Min

0.01

Adjustment Pin Current Change

=

LM117 (Note 2)

Min

1

80

66

0/0

Long-Term Stability

TJ

0.3

1

0.3

1

0/0

Thermal Resistance,
Junction-to-Case

KPackage
H Package
E Package

2.3
12
5

3
15

2.3
12

3
15

'C/W
'C/W
'C/W

Thermal Resistance, Junctlonto-Ambient (No Heat Sink)

K Package
H Package
E Package

35
140
88

125'C, 1000 hrs

1-26

35
140

'C/W

'C/W
'C/W

Electrical Characteristics

(Continued)
Specifications with standard type face are for TJ = 25·C, and those with boldface type apply over full Operating Tempera·
ture Range. Unless otherwise specified, VIN - VOUT = 5V, and lOUT = 10 rnA. (Note 3)
Parameter

LM317A

Conditions

Reference Voltage
3V ,;:; (VIN - VOUT) ,;:; 40V,
10 rnA,;:; lOUT';:; IMAX, P ,;:; PMAX

LM317

Min

Typ

Max

1.238

1.250

1.262

1.225

1.250

1.270

0.005

Min

1.20

Typ

Units
Max

1.30

V

0.Q1

0.01

0.04

%IV

0.01

0.02

0.02

0.07

%IV

10 rnA ,;:; lOUT';:; IMAX (Note 4)

0.1

0.5

0.1

0.5

%

0.3

1

0.3

1.5

%

Thermal Regulation

20 ms Pulse

0.04

0.07

0.04

0.07

%/w

50

100

50

100

",A

0.2

5

0.2

5

",A

3.5

10

3.5

10

rnA

3.4
1.8

1.5
0.5

2.2
0.8

3.4
1.8

A
A

0.15
0.075

0.4
0.2

A
A

0.003

0.003

%

65

65

dB

80

dB

Temperature Stability

TMIN ,;:; TJ';:; TMAX

Minimum Load Current

(VIN - VOUT) = 40V

Current Limit

(VIN - VOUT) ,;:; 15V
K, T Packages
H, P Packages

1.5
0.5

2.2
0.8

(VIN - VOUT) = 40V
K, T Packages
H, P Packages

0.15
0.075

0.4
0.2

RMS Output Noise, % of VOUT

10Hz,;:;f,;:; 10kHz

Ripple Rejection Ratio

VOUT = 10V, f = 120 Hz,
CADJ = 0

1

JoLF

VOUT = 10V, f = 120 Hz,
CADJ = 10 JoLF

66

1

80

66

TJ = 125·C, 1000 hrs

0.3

1

0.3

1

%

Thermal Resistance, Junctionto-Case

K Package
H Package
T Package
P Package

2.3
12
4
7

3
15
5

2.3
12
4
7

3
15

·C/W
·C/W
·C/W
·C/W

Thermal Resistance, Junctionto-Ambient (No Heat Sink)

KPackage
H Package
TPackage
P Package

35
140
50
80

·C/W
·C/W
·C/W
·C/W

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional. but do not guarantee specific performance limits. For guaranteed specifications and test conditions. see the Electrical Characteristics.
The guaranteed specifications apply only for the test conditions listed.
Note 2: Refer to RETS 117AH drawing for the LMl17AH, the RETS117H drawing for the LMI17H. the RETS117 AK drawing for the LM 117AK, or the RETSI17K for
the LM117K military specifications.
Note 3: Although power dissipation is int.rnally limit.d. thes. sp.cificatlons are appllcabl. for maximum power dissipations of 2W for the TO·39 and TO·202. and
20W for the TO·3 and TO·220. IMAX Is 1.SA for the TO-3 and T0-220 packages and 0.5A for the T0-39 and TO·202 packages. All limits (I .•.• the numbers in the
Min. and Max. columns) are guaranteed to National's AOQL (Av.rage Outgoing Quality Level).
Note 4: Regulation is measured at a constant junction temperature. using pulse testing with a low duty cycle. Changes In output voltage due to heating effecls are
covered under the specifications for thermal r.gulation.
Note 5: Human body model. 100 pF discharged through a 1.5 kll reSistor.

1-27

i:
CI.)

~
.....

~

...........
CI.)

%

Long.Term Stability

35
140
50
80

....
....
.......

i:

....

1.25

Load Regulation

10 rnA,;:; lOUT';:; IMAX
3V ,;:; (VIN - VOUT) ,;:; 40V

~
.....
r

.....
r

3V ,;:; (VIN - VOUT) ,;:; 40V (Note 4)

Adjustment Pin Current

....
....

V

Line Regulation

Adjustment Pin Current Change

r
i:

•

Typical Performance Characteristics
Output Capacitor = 0 ,.,.F unless otherwise noted
Load Regulation

Current Limit

Adjustment Current

--

60

...
l

~

Il

-OJ

IQIIT~

=
~
~

...

..

glo.SAr -

l...

I'-I;::::J' "1.&'A'-

-0.4

"
'"'"
1l
...

"-

!i"

~

-0.6

~ :.0.8

~:U; ~5~OV-

-

-1.0
-15

I' "1 I
-so -25 0

"

Dropout Voltage

w

~

.

1.0 L.....l-.l--'---'--.;,i....~~.......~
-75 -50 -Z5 0 Z5 50 75 100 125 150

I

1.250

Ti'- 5

r-...

'"

...

"

I"- 4~

m

'"

l!i

fi

I

I

..

..... CADJ

BO

\

w

V,N-VOUT = SV

..

~

lour::= 500raA

10

10

IS

ZO

31

25

25

.'11uf

-100

1k

1.5

;;;

BO

'"

60

l!i

1.0
0.6

~!

s:!
~f:

/

,.10

c

-0.5
-1.0
-1.5

.I'CADJ·,I1uf ....

wE
E!~
~s:i

>£i

10k

FREQUENCY 1Hz)

o

1I111l

10

1M

1.0
0.5

ZO

30

40

i
It:
iC

I11111

-=

CADJ'11Iuf

,11111

~

~ADJ'D

40
VIN"15V
VOUT = 10V

zo

f= 120 Hz

Tj=

2!i~1~1II

D

100

Ik

10k

lOOk

1M

0.01

0.1

IAJ:

Load Transient Response

C~ "!F: C~DJ LI~F

--

~

l!i

l~=O:CADJ'D

VOUT~ 10V

10

OUTPUT CURRENT (AI

Line Transient Response
~~

q.""50'C

100

"1"10

!:;z

~

~ ~Tj'ZS"C

1.0

o

V,N' 15V

I, \
\,

1.6

r-CADJ'~

... ~ P'

FREQUENCV (Hzl

Y,N -15V
VOUT-IOV
lour 500mA
Tj=2S'C

-

Z.5

Ripple Rejection

20

Output Impedance

11

0.5

~ 'DUT = 600 mA

40

OUTPUT VOLTAGE IV)

10-2

"

o

o

101

.

Z.O

INPUT-OUTPUT OIFFERENTIAL IV)

VOUT"OV
/' ~ Tj'2S"C
/ / ~ADJ-O '\:
:--... \

;;:

ZO -"IZ0Hz
Tj' Zi'C

o

...
~;;

1l

b: ~

Ripple Rejection
IDO

CADJ-ll1uf

'"

~

3.0

TEMPERATURE rC)

Ripple Rejection

w

Minimum Operating Current

I.ZZ0
-75 -50 -Z5 0 Z5 50 75 100 IZ5 ISO

100

iC

TEMPERATURE rC)

4.0

TEMPERATURE rCI

It:

j

C
.5 3.5

~ 1.230

40

1

4.5

:::i
ill

~
;;:

/

40

1.261

~ 1.240

&0

45

Temperature Stability
~

80

/'"

V

INPUT-OUTPUT DIFFERENTIAL IVI

2.0 ,-...-...-.,..--,--,-...,...-,.....,.....,

.

50

35
-75 -50 -Z5 0 25 50 75 100 125 ISO

Z5 50 75 100 125 150

TEMPERATURE rCI

!

55

~

:i

r/

~

10

10UT:= 50 iliA
Tj-25OC

....
,.'"

5

I I I
I I I
~~I

-I

-z
-3

...

1.5

u

0.5

1.0

I

Ct'OICA~J'~ r-

c.r-- ~ :=CL' M:CADJ'11Iuf
Y,N '15V
VOUT 'IOV

~

'NL -SOmA

T'=2S-C

!'~ J

L
II

1\ I I
IUJ..

10

10

ZO
TlMEfpsl

20

40

~

10

ZO

30

40

TIME",,)
TL/H/9063-4

1-28

r-

Application Hints
In operation, the LMl17 develops a nominal 1.25V reference voltage, VREF, between the output and adjustment terminal. The reference voltage is impressed across program
resistor Rl and, since the voltage is constant, a constant
current 11 then flows through the output set resistor R2, giving an output voltage of
VOUT = VREF (1

tween 500 pF and 5000 pF. A 1 ,...F solid tantalum (or 25 ,...F
aluminum electrolytic) on the output swamps this effect and
insures stability. Any increase of the load capacitance larger
than 10 ,...F will merely improve the loop stability and output
impedance.
Load Regulation
The LM 117 is capable of providing extremely good load regulation but a few precautions are needed to obtain maximum performance. The current set resistor connected between the adjustment terminal and the output terminal (usually 2400) should be tied directly to the output (case) of the
regulator rather than near the load. This eliminates line
drops from appearing effectively in series with the reference
and degrading regulation. For example, a 15V regulator with
0.050 resistance between the regulator and load will have a
load regulation due to line resistance of 0.050 x IL. If the
set resistor is connected near the load the effective line
resistance will be 0.050 (1 + R2/Rl) or in this case, 11.5
times worse.
Figure 2 shows the effect of resistance between the regulator and 2400 set resistor.

+ :~) + IADJR2
LM111

LM117

TL/H/9063-S

vourI ...... "'.'"
Rs

FIGURE 1
Since the 100 ,...A current from the adjustment terminal represents an error term, the LM 117 was designed to minimize
IADJ and make it very constant with line and load changes.
To do this, all quiescent operating current is returned to the
output establishing a minimum load current requirement. If
there is insufficient load on the output, the output will rise.

VIN

AOJ

or

~
.:

External Capacitors
An input bypass capacitor is recommended. A 0.1 ,...F disc
or 1 ,...F solid tantalum on the input is suitable input bypass·
ing for almost all applications. The device is more sensitive
to the absence of input bypassing when adjustment or output capacitors are used but the above values will eliminate
the possibility of problems.
The adjustment terminal can be bypassed to ground on the
LMl17 to improve ripple rejection. This bypass capacitor
prevents ripple from being amplified as the output voltage is
increased. With a 10 ,...F bypass capacitor 80 dB ripple rejection is obtainable at any output level. Increases over
10 ,...F do not appreciably improve the ripple rejection at
frequencies above 120 Hz. If the bypass capacitor is used, it
is sometimes necessary to include protection diodes to prevent the capacitor from discharging through internal low current paths and damaging the device.
In general, the best type of capacitors to use is solid tantalum. Solid tantalum capacitors have low impedance even at
high frequencies. Depending upon capacitor construction, it
takes about 25 ,...F in aluminum electrolytic to equal 1 ,...F
solid tantalum at high frequencies. Ceramic capacitors are
also good at high frequencies; but some types have a large
decrease in capacitance at frequencies around 0.5 MHz.
For this reason, 0.01 ,...F disc may seem to work better than
a 0.1 ,...F disc as a bypass.
Although the LM 117 is stable with no output capacitors, like
any feedback circuit, certain values of external capacitance
can cause excessive ringing. This occurs with values be-

vour

~~D

TL/H/9063-6

FIGURE 2. Regulator with Line Resistance
In Output Lead
With the TO-3 package, it is easy to minimize the resistance
from the case to the set resistor, by using two separate
leads to the case. However, with the TO-5 package, care
should be taken to minimize the wire length of the output
lead. The ground of R2 can be returned near the ground of
the load to provide remote ground sensing and improve
load regulation.
Protection Diodes
When external capacitors are used with any IC regulator It is
sometimes necessary to add protection diodes to prevent
the capacitors from discharging through low current points
into the regulator. Most 10 ,...F capacitors have low enough
internal series resistance to deliver 20A spikes when shorted. Although the surge is short, there is enough energy to
damage parts of the IC.
When an output capacitor is connected to a regulator and
the input is shorted, the output capacitor will discharge Into
the output of the regulator. The discharge current depends
on the value of the capacitor, the output voltage of the regulator, and the rate of decrease of VIN. In the LMl17, this
discharge path is through a large junction that is able to
sustain 15A surge with no problem. This is not true of other
types of positive regulators. For output capacitors of 25 ,...F
or less, there is no need to use diodes.

1-29

3:
....
....
~r3:
........

:::=!

r-

3:
Co)

....
~
r3:
.........
Co)

Application Hints

(Continued)
The bypass capacitor on the adjustment terminal can discharge through a low current junction. Discharge occurs
when either the input or output is shorted. Internal to the
LM117 is a. 50n resistor which limits the peak discharge

current. No protection is needed for output voltages of 25V
or less and 10 /LF capacitance. Rgure 3 shows an LM117
with protection diodes included for use with outputs greater
than 25V and high values of output capacitance.

101

LMII7

YIN

YIN

Your

Your

AOJ

HI
240

02
IN4D1Z

+

H2

T

VOUT = 1.25V (1

+

*) + IAOJR2

CI

Dl protects against Cl
D2 protects against C2

C2

rl~F

":"

TL/H/9063-7

FIGURE 3. Regulator with Protection Diodes

Schematic Diagram
r---~~--~r-----'-----1r-----t--~----------------------------t---------~-1~--~.

TUH/9063-8

1-30

rii:

....
....

Typical Applications (Continued)
SV Logic Regulator with Electronic Shutdown"

;:

......

Slow Turn-On 1SV Regulator

H~-4~~9UT
L..-.::r:----'

r-

..........;:;::....-...~f----------4~~~:T
IN4002

ii:
....
....

~
rii:

....
;:
......
w

rii:
w

~+-JVv..-TTL

lk

....
.....

'Min. output '" 1.2V

TL/H/9063-9

TL/H/B063-3

Adjustable Regulator with Improved
Ripple Rejection

High Stability 10V Regulator

~l~-"'--"

.....--~~ ~:VUT

L..-":;:::----'

Rl
2k

Dl*
lN4002

5%

R2
1.5k

1%

t50lid tantalum

-

'Discharges Cl if output is shorted to ground

TLlH/9063-10

TL/H/9063-11

High Current Adjustable Regulator
3-LMI95'S IN PARALLEL

•
~f-----f-----t-----"'-VOUT
IN4002

*

t50lid tantalum

tMinimum load current

= 30 rnA

tOptional-improves ripple rejection

1·31

TLiH/B063-12

Typical Applications (Continued)
oto 30V Regulator

Power Follower
10V-40V

LM1I7

VOUT

Cl
-:;:- O.I#....
F_

.......

INPUT -M~-+-t

Rl
10k

LM117

R2

Full output current not avaIlable at high Input-output voltages

2.4

-IOV
TL/H/9063-13

TL/H/9063-14

SA Constant Voltage/Constant Current Regulator
MJ4602

r-------------.-------.---~

R3

0.2
Rl
33

5W

~t-------_1~--------~------t_----~~~~~~V

.....--r--...

C5
75 pF

R5
330k

-BY

TL/H/9063-15

tSolld tantalum
'Lights in constant current mode

1-32

.-----------------------------------------------------------------------------'r

....
....

iii:

Typical Applications (Continued)

~
.....
r

High Gain Amplifier

1.2V-20V Regulator with
Minimum Program Current

1A Current Regulator

V·

Your·

iii:
....
....

LM111
A2

2.4

OUTPUT

AI
10k
INPUT

TUH/S063-16

LMI95

TL/H/S063-17

·Minimum load current

~

:::!
r
iii:
Co)

....

~
.....
r

iii:
Co)

....
.....

4 rnA

-=

TL/H/S063-18

Low Cost 3A Switching Regulator
01

2N3192j - - - - - - - -...,..,-~~~....

..

t-""'..,..,~I-t-----

-I.IV TO 32V

+

01
IN311D

tSolid tantalum

TUH/SOB3-IS

'Core-Arnold A·254168-2 60 turns

Precision Current Limiter

4A Switching Regulator with Overload Protection

........."",..,...-Iour .. v:.
'--"'T----'

_-_~.,.:O~~II_.

2N2905-,.._ _ _ _ _'-_-_-_.-...._-

*0.80:5: R1 :5: 1200
TLIH/S063-21

A4

AI
30

2.5

I_~'~ ~""'W'Y-"-I

a......;.~....1

A5

15k

C2
IDD.F
H6

240

+
01

IN3BID

-=

C4
lOa"Ft

tSolid tantalum
'Core-Arnold A·254168-2 60 turns

TL/H/S063-20

1·33

•

.... .-----------------------------------------------------------------------------,
~

C')

:::E

Typical Applications (Continued)

....I

....~

Tracking Preregulator
R2

C')

720

:::E
....I

j:::
....
....
:::E
....I

VOUT

~
....::E....

R3

120

....I

TUH/9063-22

Current Limited Voltage Regulator
VOUT = 1.25V (I +

OUT

~)

+ IADJR2

r-----,
I
I

I
I

TRANSFORMERS,
RECTIFIERS,
AND
FILTER
CAPACITOR

I
1L ____ .J

-Short cireuR current is approximately

60~:V, or 120 mA

TL/H/9063-23

(Compared to LMl17's higher current IimH)
- At 50 mA output only

'.4 voit of drop occurs in R3 and R4

Adjusting Multiple On-Card Regulators with Single Control·

• All outputs within

± 100 mV

tMinlmum load-10 mA

1·34

TUH/9063-24

Typical Applications (Continued)
AC Voltage Regulator

50 mA Constant Current Battery Charger

120
12Vp-p
24Vp-p

rv

lA
TL/H/9063-27

r-'\.
•
480 .~

Adjustable 4A Regulator

TL/H/9063-25

12V Battery Charger

........,.".>h~....-4.5V TO 25V

5.

5.
TL/H/9063-26

• Rs-set. output impedance of charger: ZOUT

= Rs ( 1 +

1*)

Use of Rs allows low charging rate. with fully charged battery.
TL/H/9063-28

•

Current Limited 6V Charger

9VTO~
240

'Sets peak current (O.SA for 10)
"The 1000 ,..F Is recommended to filter out Input
transients

Uk
100

2N2222

1*

TLlH/9063-29

1·35

.... r---------------------------------------------------------------------------------,

~

('I)

:E

Connection Diagrams

....I

....~

(TO·3)
Metal Can Package

('I)

:E

(TO·39)
Metal Can Package

....I

o---"~---INPUT

r:::
....
....

:E

....I

~....
....
:E

O--~<----

OUTPUT
TL/H/9063-31

CASE IS OUTPUT

Bottom View

....I

TLiH/9063-30

Order Number LM117 AH, LM117AH/883, LM117H,
LM117H/883, LM317AH or LM317H
See NS Package Number H03A

Bottom View
Steel Package
Order Number LM117AK STEEL, LM117AK/883,
LM117K STEEL, LM117K STEEL/883,
LM317AK STEEL or LM317K STEEL
See NS Package Number K02A
Aluminum Package
Order Number LM317KC
See NS Package Number KC02A

(TO·220)
Plastic Package

0

(TO·202)
Plastic Package

-

0

.- Your
""L

OUTPUT

I
2

1

20

10

11

12

VOUT

I"'"

I

INPUT

I

TLiH/9063-34

ADJ

AOJ

---

-

-

Top View
_ _ VI

N

LVOUT

VOUT

TLiH/9063-33
TL/H/9063-32

Front View
Order Number LM317AT or LM317T
See NS Package Number T03B

Front View
Order Number
LM317AMP or LM317MP
See NS Package Number P03A

1-36

Order Number LM117E/883
See NS Package Number E20A

~National

~ Semiconductor

LM117HV/LM317HV 3-Terminal Adjustable Regulator
General Description
The LM117HVILM317HV are adjustable 3-terminal positive
voltage regulators capable of supplying in excess of 1.SA
over a 1.2V to S7V output range. They are exceptionally
easy to use and require only two external resistors to set the
output voltage. Further, both line and load regulation are
better than standard fixed regulators. Also, the LM117HV is
packaged in standard transistor packages which are easily
mounted and handled.
In addition to higher performance than fixed regulators, the
LM117HV series offers full overload protection available
only in IC's. Included on the chip are current limit, thermal
overload protection and safe area protection. All overload
protection circuitry remains fully functional even If the adjustment terminal is disconnected.
Normally, no capacitors are needed unless the device is
situated more than 6 inches from the input filter capacitors
in which case an input bypass is needed. An optional output
capacitor can be added to Improve transient response. The
adjustment terminal can be bypassed to achieve very high
ripple rejections ratios which are difficult to achieve with
standard 3-terminal regulators.
Besides replacing fixed regulators, the LM117HV is useful In
a wide variety of other applications. Since the regulator Is
"floating" and sees only the Input-to-output differential voltage, supplies of several hundred volts can be regulated as
long as the maximum Input to output differential is not exceeded, I.e. do not short the output to ground.

Also, it makes an especially simple adjustable switching regulator, a programmable output regulator, or by connecting a
fixed resistor between the adjustment and output, the
LM117HV can be used as a precision current regulator.
Supplies with electronic shutdown can be achieved by
clamping the adjustment terminal to ground which programs
the output to 1.2V where most loads draw little current.
The LM117HVK STEEL and LM317HVK STEEL are packaged in standard TO-3 transistor packages, while the
LM117HVH and LM317HVH are packaged in a solid Kovar
base TO-39 transistor package. The LM317HVT uses a TO220 plastic package. The LM117HV is rated for operation
from -SS'C to +1S0'C, and the LM317HV from O'C to
+ 12S'C.

Features
•
•
•
•
iii
I!I

•
•
•
•
•

Adjustable output down to 1.2V
Guaranteed 1.SA output current
Line regulation typically 0.01 %IV
Load regulation typically 0.1 %
Current limit constant with temperature
100% electrical burn-In
Eliminates the need to stock many voltages
Standard 3-lead transistor package
80 dB ripple rejection
Output Is short-circuit protected
P+ Product Enhancement tested

Typical Applications
1.2V-45V Adjustable Regulator

Digitally Selected Outputs

5V Logic Regulator with
Elsctronlc Shutdown'
LM1nHV

H -.....VOUT"

TL/H/9062-1

Full output current not bvallable
at high Input·output voltages
tOptlonal-lmproves transient response. Output
capacitors In the range of 1 ,..F to 1000 ,..F of
aluminum or tantalum electrolytic are commonly
used to provide Improved output Impedance and
relection of transients.
'Needed If device Is more than 6 Inches from
filter capaCitors.
ttVOUT = 1.25V (1 +

TL/H/90B2-3
INPUTS

'Min. output'" 1.2V
TL/H/90B2-2

'Sets maximum VOUT

*) + IADJ R2

1-37

•

>
::J:

........

CO)

:::E

....I

>
....
::J:

........

:::E

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 3)
Power Dissipation
Internally limited
Input-Output Voltage Differential
+60V. -0.3V

Operating Junction Temperature Range
-55·Cto
LMl17HV
LM317HV
O"Cto
-65·C to
Storage Temperature
Lead Temperature (Soldering. 10 sec.)
ESD Tolerance (Note 4)

+ 150"C
+ 125·C
+ 150·C
300·C
2000V

....I

Electrical Characteristics (Note 1)
Parameter

LM117HV

Conditions

Min
Line Regulation

TJ = 25·C.3V ::;: VIN - VOUT ::;: 60V
(Note 2) IL = 10 mA

Load Regulation

TJ

Thermal Regulation

TJ

= 25·C. 10 mA ::;: lOUT::;: IMAX
= 25·C. 20 ms Pulse

10mA::;: IL::;: IMAX
3.0 V ::;: (VIN - VOUT) ::;: 60V

Reference Voltage

3.0 V ::;: (VIN - VOUT) ::;: 60V. (Note 3)
10 mA::;: lOUT::;: IMAX. P::;: PMAX

Line Regulation

3.0V ::;: (VIN - VOUT) ::;: 60V.IL

Load Regulation

10 mA ::;: lOUT::;: IMAX (Note 2)

Temperature Stability

TMIN ::;: TJ ::;: TMAX

Minimum Load Current

(YIN - VOUT)

Current Limit

(VIN - VOUT) ::;: 15V
K. T Packages
H Package
(VIN - VOUT) ::;: 60V
K. T Packages
H Package

RMS Output Noise. % of VOUT
Ripple Rejection Ratio
Long-Term Stability
Thermal Resistance.
Junction to Case

Typ

Max

0.Q1

0.02

0.01

0.04 %IV

0.1

0.3

0.1

0.5

50

100

50

100

p.A

0.2

5

0.2

5

p.A

0.02 0.05
0.3

0.3

1.5
0.5

TJ

H Package
TPackage
K Package

Thermal Resistance.
H Package
Junction to Ambient (no heat sink) TPackage
KPackage

66

1.5

%

3.5

12

mA

2.2
0.8

3.7
1.9

A
A

1

3.5

7

2.2
0.8

3.5
1.8

V

0.02 0.07 %IV

1

1

= 60V

%

0.04 0.07 %/W

1.20 1.25 1.30 1.20 1.25 1.30

= 10 mAo (Note 2)

= 25·C.l0Hz::;: f::;: 10kHz
VOUT = 10V. f = 120 Hz
CADJ = 10 p.F
TJ = 125·C

Units

Max Min

0.03 0.07

Adjustment Pin Current
Adjustment Pin Current Change

LM317HV

Typ

1.5
0.5

%

0.3
0.03

0.3
0.03

A
A

0.003

0.003

%

65
80

dB
dB

65
80
0.3

66
1

12

15

2.3

3

140
35

0.3
12
4
2.3
140
50
35

1

%

15
5
3

·C/W

·C/W
·C/W
·C/W
·C/W
·C/W

Note 1: Unless otherwise spacHied. these specHicetlonsapply: -55'C';; TJ ,;; +15O'Cfortha LMI17HV. and O'C';; TJ ,;; + 125'C for the LM317HV;VIN - VOUT

= 5V and lOUT = O.IA for the T0-39 package and lOUT = 0.5A for the TO-3 and TO·22O packages. Although power dissipation is internally IimHed. these
specificetions are appliceble for power dissipations of 2W for the T0-39 and 20W for the T0-3 and TO·220. IMAX is 1.5A for the TO·3 and TO·220 and 0.5A for the
T0-39 package.
Note 2: Regulation is measured at constant junelion temperature. Changes in output voltage due to heating effects must be taken into account separately. Pulse
testing with low duty cycle is used.
Not. 3: Refer to RETS117HVH for LMI17HVH or RETSI17HVK for LM117HVK military specificetioins.
Note 4: Human body model. 1.5 kG in series with 100 pF.

1-38

Typical Performance Characteristics
Output capacitor = 0 ,.,.F unless otherwise noted.
Load Regulation

Current Limit

Adjustment Current

0.2

£

Ill. o.lA

zQ

:i

...
~
~

.,.~
.~

t--

...~

50

!&
~

45

.3

~ .....
Il·1.5~,

-0.2

.....

60

z

-0.6

.a

f- ~~~~ ~5~OV

-0.8

'j' 'I I

-1.0
-75 -50 -25 0 25 50 75 100 125 150

10

3D

20

50

40

Dropout Voltage

35
-75 -50 -25 0 25 50 75 100 125 150

60

TEMPERATURE (' C)

Minimum Operating Current

1.260

~VOUT

..

s:

.

g
~

I""-

I--'

!:;

1.240

\

~ 1.230

3.5

0-

3,0

...~

2.5

~

1.5

z

:;

"
1.0 '-.l--'-...J...--'-~.:......_~.I.,...;:II
-75 -50 -25 0 25 50 75 100 125 150

Ripple Rejection

~
~

.1
L
r---.. ~J'O

a:

lii
3

1;

6IJ

i

1

40

~
~

VIN-VoUT' 5V
Il-500mA
20
-'-120H.
Ti" 25'C

I

o

o

10

15

..........

a:

25

3D

20

o

35

10

100

Ik

VIN -15Y
VoUT '10V
Il"&OOmA
Ti- 25'C

10- 3
10

100

WI

....
~!

-0.5

C)

-1.0

>j:

....

,/

-1.5
.I'CAoJ"I11pF"""

11.1

S;

~~i
!~c
>G

10k

FREQUENCY (H.)

lOOk

1M

Ic!

1.•

0.5

~~

Ik

.ti
z

\

10k

lOOk

80

I
o

1.0
0.5

0

A

-11F;

:111111111
CAoJ"IIIpF

:;:

=
~
=

40

C~oJt I~F

Load Transient Response

.....
.....

I I
f-- f--

>-

5~
~~

Il-SOmA

Ti" 25"C

S
....
ill
=
~

I
I

I

-I
-2
-3
15
1.0
0.•

f--

~
IV

I I

j'OtAf~ t-~Cl = M; CAoJ " 1M f:VIN '15V
VoUT 'IOV
INLaSDmA
Tj=25'C

1\ LI

I
II

1\ 1 1
1U J.

c

10

20
TIME",,)

30

40

10

0.1
OUTPUT CURRENT (A)

~

r/

II

Ti"25,~,

0.01

"'i!~

[\,!:l-O;CAoJ-O

IIII

~AoJ"O

VIN-15V
VoUT-IOV
20 r,= 120 H.

o

1M

:i

"

60

~

YOUT ~ ID~

40

30

20

10

r-

Line Transient Response
1.&

-

0.5

FREQUENCY (H.)

Output Impedance

CAoJ =~

lii
3

~

OUTPUT VOLTAGE (V)

==r--

~ ~Ti'25'C

1.0

Ripple Rejection

'"\.""

40

r

.-f-~

~:I5O'C
I

100

Il =500mA
VIN' 15V
80
VoUT "lOY
Ti" 25'C
.........CADJ=O I~
1//
60

/

~

INPUT -OUTPUT DIFFERENTIAL (V)

I
I
CAoJ - 10"F
1"---.

II:

20

2.0

Ripple Rejection
100

CAoJ·1M

II:

b: ~

TEMPERATURE ( CI

100
80

I I
Ti--5

o

1.220
-75 -50 -25 0 25 50 75 100 125 150

TEMPERATURE ( C)

4.5
4.0

,!;

~

"-

~

z

/

40

Temperature Stability

,-r--r-...,....'T""'T'""""""''''''''''
.. 100 mV

ii 1.250

lii
3

I

INPUT-OUTPUT DIFFERENTIAL (v)

TEMPERATURE ( CI

3.0

/v

ill

-0.4

0-

I""'"" f-

55

c

~

10

20

3D

40

TIME (,us)
TLlH/9062-4

1-39

>

::c

."'CO)"

~

>:
~
..-

::iil
....

r-----------------------------------------------------------------------,
Application Hints
In operation, the LM117HV develops a nominal 1.25V reference voltage, VREF, between the output and adjustment terminal. The reference voltage is impressed across program
resistor R1 and, since the voltage is constant, a constant
current 11 then flows through the output set resistor R2, giving an output voltage of
VOUT = VREF (1

tance can cause excessive ringing. This occurs with values
between 500 pF and 5000 pF. A 1 /loF solid tantalum (or 25
p.F aluminum electrolytic) on the output swamps this effect
and insures stability. Any increase of load capacitance larger than 10 p.F will merely improve the loop stability and
output impedance.

+ :~) + IAOJR2

Load Regulation
The LM117HV is capable of providing extremely good load
regulation but a few precautions are needed to obtain maximum performance. The current set resistor connected between the adjustment terminal and the output terminal (usually 2400) should be tied directly to the output of the regulator rather than near the load. This eliminates line drops from
appearing effectively in series with the reference and degrading regulation. For example, a 15V regulator with 0.050
resistance between the regulator and load will have a load
regulation due to line resistance of 0.050 x IL. If the set
resistor is connected near the load the effective line resistance will be 0.050 (1 + R2/R1) or in this case, 11.5 times
worse.
Figure 2 shows the effect of resistance between the regulator and 2400 set resistor.

LMII7HV

TL/H/9082-5

LM117HV

FIGURE 1
Since the 100 p.A current from the adjustment terminal represents an error term, the LM117HV was designed to minimize IADJ and make It very constant with line and load
changes. To do this, all quiescent operating current is returned to the output establishing a minimum load current
requirement. If there Is insufficient load on the output, the
output will rise.

V,N

.I

RS
vOUTI-"",."....-VOUT
AOJ
I

RI
240

External Capacitors
An input bypass capacitor Is recommended. A 0.1 p.F disc
or 1 p.F solid tantalum on the Input Is suitable input bypassing for almost all applications. The device Is more sensitive
to the absence of Input bypassing when adjustment or output capacitors are used but the above values will eliminate
the posslbllty of problems.
The adjustment terminal can be bypassed to ground on the
LM117HV to Improve ripple rejection. This bypass capacitor
prevents ripple from being amplified as the output voltage Is
Increased. With a 10 p.F bypass capacitor eo dB ripple rejection Is obtainable at any output level. Increases over 10
p.F do not appreciably Improve the ripple rejection at frequencies above 120 Hz. If the bypass capacitor Is used, It Is
sometimes necessary to Include protection diodes to prevent the capacitor from discharging through Internal low current paths and damaging the device.
In general, the best type of capacitors to use are solid tantalum. Solid tantalum capacitors have low Impedance even at
high frequencies. Depending upon capacitor construction, it
takes about 25 p.F In aluminum electrolytic to equal 1 p.F
solid tantalum at high frequencies. Ceramic capacitors are
also good at high frequencies; but some types have a large
decrease in capacitance at frequencies around 0.5 MHz.
For this reason, 0.Q1 /loF disc may seem to work betler than
a 0.1 p.F disc as a bypass.
Although the LM117HV is stable with no output capacitors,
like any feedback circuit, certain values of external capaci-

TL/H/9082-6

FIGURE 2. Regulator with Line
Resistance In Output Lead
With the TO-3 package, It Is easy to minimize the resistance
from the case to the set resistor, by using two separate
leads to the case. However, with the TO-5 package, care
should be taken to minimize the wire length of the output
lead. The ground of R2 can be returned near the ground of
the load to provide remote ground sensing and Improve
load regulation.
Protection Diodes
When external capaCitors are used with any 10 regulator It Is
sometimes necessary to add protection diodes to prevent
the capacitors from discharging through low current points
Into the regulator. Most 10 p.F capaCitors have low enough
Internal series resistance to deliver 20A spikes when shorted. Although the surge is short, there Is enough energy to
damage parts of the IC.
When an output capaCitor is connected to a regulator and
the Input Is shorted, the output capaCitor will discharge Into
the output of the regulator. The discharge current depends
on the value of the capaCitor, the output voltage of the regulator, and the rate of decrease of Y,N. In the LM117HV, this
discharge path is through a large junction that is able to
sustain 15A surge with no problem. This is not true of other
types of positive regulators. For output capacitors of 25 p.F
or less, there Is no need to use diodes.

1-40

The bypass capacitor on the adjustment terminal can discharge through a low current junction. Discharge occurs
when either the input or output is shorted. Internal to the
LM117HV is a 500 resistor which limits the peak discharge
current. No protection is needed for output voltages of 25V
or less and 10 poF capacitance. Figure 3 shows an
LM117HV with protection diodes included for use with outputs greater than 25V and high values of output capacitance.

~
....
....
......
::J:
,<

0'
1N4DDZ

v,.

H---.....- -....-VOUT

r-

s:::

....
......
Co)

02
1N4002

Current Limit

R2

Internal current limit will be activated whenever the output
current exceeds the limit indicated in the Typical Performance Characteristics. However, if during a short circuit condition the regulator's differential voltage exceeds the Absolute Maximum Rating of 60V (e.g. VIN ;" 60V, VOUT = OV),
internal junctions in the regulator may break down and the
device may be damaged or fail. Failure modes range from
an apparent open or short from input to output of the regulator, to a destroyed package (most common with the TO-220
package). To protect the regulator, the user is advised to be
aware of voltages that may be applied to the regulator during fault conditions, and to avoid violating the Absolute Maximum Ratings.

::J:

<

r'M
+

C2

TLlH/9062-7

FIGURE 3. Regulator with Protection Diodes
VOllT

= 1.25V ( 1 +

1*) +

IADJR2

Dl protects against Cl
D2 protects against C2

Schematic Diagram

II
TUH/9062-8

1-41

>
::c
....

....

CO)

~

>
::c
....

....
....
:i

Typical Applications (Continued)
Slow Turn-On 15V Regulator

Adjustable Regulator with Improved
Ripple Rejection

LM11lHV

.....,...----........ ~fJ'T

'--.::;:::.--'

RI
240
IN4002

CI

25.F

TL/H/9062-9

TL/H/9062-IO

tSolid tantalum
-Discharges Cl if output is shorted to ground

High Stability 10V Regulator

High Current Adjustable Regulator
3-lMI95'S IN PARALLEL

I-tt--......~ ~~J'T

'"-""'i...-....

RI
Zk
6%

R3

2N2.05-,..._ _...._ _..I\I50\lO~_.......
HZ
I.5k

1%

---+--....

H~-....

VOUT

TL/H/9062-11

TL/H/9062-12

tSolid tantalum
·Minimum load current

= 30 rnA

*Optlonal-lmproves ripple rejection

oto 30V Regulator

Power Follower
IOV-40V

""'''''"+-1
Rl

INPUT .....

10k

LM111HV

R2
2.4

R3

680
-IOV

TLlH/9062-13

TL/H/9062-14

Full output current not available
at high input-output voltages

1-42

Typical Applications

(Continued)

SA Constant Voltage/Constant Current Regulator
MJ4502

r---------------~--------4---~
CURRENT
ADJUST
Rl
33
35V - . .J\oM..-......

R2
250k

R3
0.2
5W

t-....- - - -.....- - -....~~f---~~--+-~.~~~~~V

'--~::.-...I

C3

10" Ft

C5
75 pF

tSolid tantalum
·lights in constant current mode

l
+

R5
330k

-6V

TLlH/9062-15

1A Current Regulator

1.2V-20V Regulator with
Minimum Program Current

•

TLlH/9062-16
TLlH/9062-17

-Minimum load current::::: 4 rnA

1·43

Typical Applications (Continued)
High Gain Amplifier

Low Cost SA Switching Regulator
Ql
2N~gI2________________-e.J-:-~-!~~~-,

II'
LM117HV

R2

BV-J5V

2.4

~~""""'''-I

. . ."",..,....-t--------....

-I.IV TO 32V

+
Rl
l1Jlc
INPUT ...JW'Y-+-I

01
lN3880

TLlH/9062-18

tSolid tan1alum

TLlH/9062-19

'Core-Amold A-254168-2 60 lums

4A SWitching Regulator with Overload Protection

Precision Current Limiter
Y,N

!.-J

LM3t7HV ~
VOUT
IOIIT _ v.."
ADJ
_
Rl
RI

V,N

2N2905-,. _______::::~::~'Io5RI\,~,..,...

I
TLlH/9062-21

'O.8n ,; Rl ,; 120n

R4

2.&

Tracking Preregulator
R2

R&
15k

C2
101,F

120

..........-..,-r-...--,-,",-~......._VOUT
L1

1.8V TO 32V

8DDiJH*

RI

240

VIN

+
01
IN3881

C4
lOo.Ft

.R4

OUTPUT
ADJUST

TLlH/9062-22

tSolid tantalum

TLlH/9062-20

'Core-Arnold A-254168-2 60 turns

Adjustable Multiple On-Card Regulators
with Single Control·

......_-+_____.... ________ JI
'All outputs within ± 100 mV
tMinimum load-l0 mA
TLlH/9062-23

1-44

r-----------------------------------------------------------------------------~ ~

iii:
.....
.....
......

Typical Applications (Continued)
AC Voltage Regulator

:::z::

Adjustable 4A Regulator

~

!i:w
.....
......

:::z::

120

<
12Vp·p
lA

24Vp·p

rv

410

. "'"""
l"""'\

•

I-"t-'''''''''''-+-- 4.5V TO 25V
5k

TL/H/9062-24

12V Battery Charger
LM317HV

5k

1000 IlF**

TL/H/S062-27

-• As-sets oulpullmpedance of charger loUT

VIN
9VT060V

TL/H/S082-26

= As ( 1 + ~)

240

--

Use of AS allows low charging rates with fully charged battery.
"The 1000 ,.F Is recommended to flltet out Input transients

Uk

50 mA Constant Current BaHery Charger
LM317HV
VIN--1 VIN

ADJVOUT~
I

r_

1*

TL/H/S062-26

'Sets peak current (0.6A for 10)
"The 1000 ,.F Is recommended to filter out Input transients

TLlH/9082-26

1·45

•

>r-----------------------------------------------------------------,
.....
Connection Diagrams (See Physical Dimension section for further information)
....

::E:

CO)

:&i

...I

>
.....

(To-3 Steel)
Metal Can Package

(TO-39)
Metal Can Package

::E:

........

0----"'..--

:5

O--~L--

INPUT

OUTPUT
TL/H/9062-30

Case is Output
Bottom View

TL/H/9062-29

Case is Output
Bottom View

Order Number LM117HVH,
orLM317HVH
See NS Package Number H03A

Order Number LM117HVK STEEL,
LM317HVK STEEL
See NS Package Number K02A
(To-220)
Plastic Package

0
I
ADJ

+- Your

I

-

I
I---

VOUT
TL/H/9062-31

Front View
Order Number LM317HVT
See NS Package Number T03B

1-46

r-------------------------------------------------------------------------,~

....
N

i:

~National

~
~
i:
Co)

~ Semiconductor

N
Q

LM 120/LM320
Series 3-Terminal Negative Regulators
General Description

Features

The LM120 series are three-terminal negative regulators
with a fixed output voltage of -SV, -12V, and -1SV, and
up to 1.SA load current capability. Where other voltages are
required, the LM137 and LM137HV series provide an output
voltage range of -1.2V to -47V.

•
•
•
•

The LM120 need only one external component-a compensation capacitor at the output, making them easy to apply.
Worst case guarantees on output voltage deviation due to
any combination of line, load or temperature variation assure satisfactory system operation.

Preset output voltage error less than ±3%
Preset current limit
Internal thermal shutdown
Operates with input-output voltage differential down to
1V
• Excellent ripple rejection
• Low temperature drift
• Easily adjustable to higher output voltage
LM120 Series Packages and Power Capability

Exceptional effort has been made to make the LM120 Series immune to overload conditions. The regulators have
current limiting which is independent of temperature, combined with thermal overload protection. Internal current limiting protects against momentary faults while thermal shutdown prevents junction temperatures from exceeding safe
limits during prolonged overloads.

Device
LM120/LM320

Although primarily intended for fixed output voltage applications, the LM 120 Series may be programmed for higher output voltages with a simple resistive divider. The low quiescent drain current of the devices allows this technique to be
used with good regulation.

Package

Rated
Power
Dissipation

Design
Load
Current

TO-3(K)

20W

1.SA

TO-39 (H)

2W

O.SA

LM320

TO-220m

15W

1.SA

LM320M

TO-202(P)

7.SW

O.SA

Typical Applications
Dual Trimmed Supply

+ INPUT

Fixed Regulator

r--.....- .....----....-o +5.DV
6-JVl.III-_<

I.

OUTPUT

01
IN4DDI

TL/H/7767 -2

'Required if regulator is separated from filter capacitor by more than 3' . For
value given, capaCitor must be solid tantalum. 25 I'F aluminum electrolytic
may be substituted.
tRequired for stability. For value given, capacitor must be solid tantalum. 25
I'F aluminum electrolytic may substituted. Values given may be increased
without limit.

DZ
IN4001

- INPUT

For output capaCitance in excess of 100 I'F, a high current diode from
input to output (I N400l, etc.) will protect the regulator from momentary
input shorts.

~-"'-"'-+--+-O-5.ZV

TLlH/7767 -3

1-47

•

LM120/LM320

-5 Volt Regulators (Note 3)
Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 5)
Power Dissipation
Intemally limited
-25V
Input Voltage

25V

Input-Oulput Voltage Differential

See Note 1

Junction Temperatures

-65·C to

Storage Temperature Range
lead Temperature (Soldering. 10 sec.)
Plastic

+ 150·C
300·C
2600C

Electrical Characteristics
Order Numbers

LM120K-5.0

Design Output Current (ID)

(T0-3)
1.5A

1.5A

O.5A

O.5A

1.5A

O.5A

IUnits

Output Voltage

.;..
Q)

Note 1: This specificaIion applies over -55"C 0<: TJ 0<: +15O"C for the LM120 and II'C 0<: TJ 0<: +125"C for the lM32O.
Note 2: Regulation is measured at constant junction temperature. Changes in ouIput voIIage due to heating . . - must be taken into account separately. To ensure constant iunCiion temperature, low duly cycle, pulse testing is
used. The LM120/LM320 - . . . does have low thermalfeedbadc, improving line and load regulation. On 811_ tests. even though power dissipation is internally limited, electrical specifications apply only up to Po.
Note 3: For -5'1 3 amp regulators, see LM145 data &heeL
Note 4: Thermal resistance of typically 85"C1W fm 400 linear feet air flow). 22lf'CIW fon sialic air) junction to ambient. of typically 21"C/W junction to case.
Note 5: Refer to RETS12D-5H drawing for LM120H-5..D or RETS12D-5K drawing for LM120-5K nuTIIaIy specificaIions.

-12 Volt Regulators
Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and speclflcatlons_
(Note 4)
Power Dissipation

Input-Output Voltage Differential

See Note 1

Storage Temperature Range

- 65'C to

+ 150'C

Lead Temperature (Soldering, 10 sec.)

Internally Limited

Input Voltage

30V

Junction Temperatures

300'C

-35V

Electrical Characteristics
Metal Can Package
LM120K-12
(TO-3)

LM320K-12
(TO-3)

LM120H-12
(TO-39)

LM320H-12
(TO-39)

LM320T-12
(TO-220)

LM320MP-12
(TO-202)

Design Output Current (10)
Device Dissipation (Po)

1A
20W

1A
20W

O.2A
2W

O.2A
2W

1A
15W

O.5A
7.5W

Parameter

~

Conditions (Note 1)

Output Voltage

TJ = 25'C, VIN = 17V,
ILOAD = 5mA

Line Regulation

TJ = 25'C,ILOAD = 5 mA,
VMIN ,;; VIN ,;; VMAA

Input Voltage

CD

Power Plastic Package

Order Numbers

Min

Typ

f=120Hz

Load Regulation,
(Note 2)

TJ = 25'C, VIN = 17V,
5mA,;; ILOAD';; ID

Output Voltage,
(Note 1)

14.5V ,;; VIN ,;;; VMAA,
5 mA ,;;; ILOAD ,;;; ID, P ,;; PD

Min

Typ

Max

Min

Typ

Max

Min

Typ

Max

Min

Typ

Max

Min

Typ

Max

-12.3 -12 -11.7 -12.4 -12 -11.6 -12.3 -12 -11.7 -12.4 -12 -11.6 -12.4 -12 -11.6 -12.5 -12 -11.5
4
-32

Ripple Rejection

Max

56

10
-14

80
30

-12.5

4
-32
56

80

20
-14

80
30

-11.5 -12.6

4
-32
56

80

10
-14

80
10

-11.4 -12.5

4
-32
56

25

20
-14

80
10

-11.5 -12.6

4
-32
56

40

20

30

-11.4 -12.6

56
80

Quiescent Current

VMIN ,;; VIN ,;;; VMAA

2

4

2

4

2

4

2

4

2

4

TJ = 25'C
VMIN ,;; VIN ,;;; VMAA
5mA,;; ILOAD';;; ID

0.1
0.1

0.4
0.4

0.1
0.1

0.4
0.4

0.05
0.03

0.4
0.4

0.05
0.03

0.4
0.4

0.1
0.1

0.4
0.4

400

Long Term Stability

12

Thermal Resistance
Junction to Case
Junction to Ambient

400
120
3
35

12

400

400
120
3
35

12

120
Note 3
Note 3

12

24
-14.5

80
40

-11.4 -12.6

Quiescent Current
Change

Output Noise Voltage T A = 25'C, Cl = 1 ,..F, Il = 5 mA,
VIN = 17V, 10 Hz';; f,;; 100 kHz

4

-14.5 -32
80

Units

V
mV
V
dB

100

mV

-11.4

V

4

mA

2

0.05 0.3
0.04 0.25

mA
mA

400

400

,..V

120

24

24

mV

Note 3
Note 3

4
50

12
70

'CfW
'CfW

Note 1: This specification applies over -55'C ,;; TJ ,;; + 150'C for the LM120 and O'C ,;; TJ ,;; +125'C for the LM320.
Note 2: Regulation is measured at constant junction temperature. Changes in output voltage due to heating effects must be taken into account separately. To ensure constant junction temperature, low duty cycle, pulse testing is

used. The LM120/LM320 series does have low thermal fee.dback, improving line and load regulation. On all other tests, even though power dissipation is internally limited, electrical specifications apply only up to Po.
Note 3: Thermal resistance of typically 85'C/W (in 400 linear feellmin air flow), 224'C/W (in static air) iunction to ambient, of typically 21'C/W iunction to case.
Note 4: Refer to RETS120H-12 drawing for LM120H·12 or RETS120·12K drawing for LM120K-12 military specifications.
-

-

O~£W'/OUW'

II

LM120/LM320

-15 Volt Regulators
Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 4)

Input-Output Voltage Differential

Input Voltage
LM120/LM320
LM320T ILM320MP

See Note 1

Storage Temperature Range

-65"C to

+ 150"C

Lead Temperature (Soldering, 10 sec.)

Internally Limited

Power Dissipation

30V

Junction Temperatures

300"C

-40V
-35V

Electrical Characteristics
Metal Can Package
lM120K-15
(TO-3)

lM320K-15
(TO-3)

lM120H-15
(TO-39)

lM320H-15
(TO-39)

lM320T-15
(TO-220)

lM320MP-15
(TO-202)

Design Output Current (10)
Device Dissipation (Po)

1A
20W

1A
2DW

O.2A
2W

D.2A
2W

1A
15W

O.5A
7.5W

Parameter

&.

Power Plastic Package

Order Numbers

Conditions (Note 1)

Output Voltage

TJ = 25"C, VIN = 20V,
ILOAD = 5mA

Line Regulation

TJ = 25"C, ILOAD = 5 rnA,
VMIN ,;: VIN ,;: VMAX

o

Min

Typ

Max

Typ Max

5

10

Ripple Rejection

f=120Hz

56

Load Regulation,
(Note 2)

TJ = 25"C, VIN = 20V,
5mA,;: ILOAD';: 10

Output Voltage,
(Note 1)

17.5V ,;: VIN ,;: VMAX,
5 rnA ,;: ILOAD ,;: 10, P ,;: Po

5

-17

-35

-35

-15.5

30

-14.5 -15.6

Quiescent Current

VMIN ,;: VIN ,;: VMAX

2

4

TJ = 25"C
VMIN ,;: VIN ,;: VMAX
5mA';: ILOAD';: 10

0.1
0.1

0.4
0.4

Output Noise Voltage T A = 25"C, CL = 1 ).LF, IL = 5 rnA,
VIN = 20V, 10 Hz,;: f ,;: 100 kHz

400

Long Term Stability

15

2.
0.1
0.1

Min

+ 150°C for the LM120 and O°C

S

TJ

80

Typ

5
-35
56

25

10

Max

Min

Typ

80
10

5

20
-17

-14.5 -15.6

Max

Min

-35

Typ Max

56
40

-17.5 -35
80
30

-14.4 -15.7

56
80

4

2

4

2

4

0.4
0.4

0.05

0.4
0.4

0.05
0.03

0.4
0.4

0.1
0.1

0.4
0.4

400

15

15

150

400
150

15

Note 3
Note 3

400

30
-17.5

80
40

-14.3 -15.7

2

0.03

5

20

4

3
35
S

10

80

400

3
35
S

Max

-17

-35

-14.4 -15.5

150

Thermal Resistance
Junction to Case
Junction to Ambient
TJ

Typ

5

56

80

80

30

20
-17

56

80

Quiescent Current
Change

S

Min

-15.3 -15 -14.7 -15.4 -15 -14.6 -15.3 -15 -14.7 -15.4 -15 -14.6 -15.5 -15 -14.5 -15.6 -15 -14.4

Input Voltage

Note 1: This specification epplies over -55°C

Min

Units

2

V
mV
V
dB

100

mV

-14.3

V

4

rnA

0.05 0.3
0.04 0.25

rnA
rnA

400

).LV

150

.30

30

rnV

Note 3
Note 3

,4
50

12
70

"C/W
"C/W

+ 125°C for the LM320.

Note 2: Regulation is measured at constant junction temperature. Changes in output voltage due to heating effects must be taken into account separately. To ensure constant junction temperature, low duty cycle, pulse testing is
used. The LM120/LM320 series does have low thermal feedback, improving line and load regulation. On all other tests, even though power dissipation is internally limited, electrical specifications apply only up to PD.

Note 3: Thermal resistance of typically 85"C/W (in 400 linear feetlmin air flow), 224°C/W (in static air) junction to ambient, of typically 21°C/W junction to case.
Note 4: Refer to RETS120·15H drawing for LM120H·15 or RETS120·15K drawing for LM120K·15 military specifications.
-

-

-

--

-

-

r

s::
....

Typical Performance Characteristics

N

C)
......

Output Voltage vs
Temperature
1.01

~
N

Ripple Rejection
(All Types)

1
I I
V~UT ~12VIAND::;; ~

~ 1.00

r:.

~ 0,99S

r-

~O.990

.'"

1.01

~

1.005

~

1.00

;;;

'"
i:i

VIN-V

....
i; 0.995

~ ::. f--

-50 -25 0

80

1

ViUT '1- 5

25

..:;J

60

lI:
l2

40

I

I

~

20
o.DIk

50 75 100 125 150

10- 2
D.lk

Ik

2.5

~

!;
~

Minimum Input-Output
Differential TO-3 and
TO·220 Packages

2.1
1.9

Tj'1511"C

"

-,.... .....V

,-

1.1

T, -2S'C-

t;:

~

o

T, -15O'C •

..

0.95
0.9
5

..s
....

i
....
i5

1.05
1.0

15

20

25

I
I

0.25

0.5

0.75

1.0

1.25

i--'

iii5

lM120·5

1.3
1.2

3D

INPUT VOLTAGE IVI

35 40

1---

I
10k

loOk

1M

2.0

~

1.8

">

1.4

~

12
1.0

!;

~

!l

Minimum Input·Output
Differential TO·5 and
TO-202 Packages

u

o.B

L

r---:

~

""Tj '1511"0"-

0.6
0.4
1.5

~

r--r-- Tj' 25"1:
Tj-SSOC
J,

o

0.1

01

I

1
I

0.3

oA

0.5

OUTPUT CURRENT IAI

Maximum Average Power
Dissipation (TO-3)

~~

- I

I---"""

TI " 25°C

--r
I

1.0

"

T"b

..".

V

1.1

0.9

10

I
I

Quiescent Current vs
Load Current

- ,~ • ~S5"~

1.15

i
Ik

OUTPUT CURRENT IAI

lM120·5

-

Tj'25"c-

0.5

Quiescent Current vs
Input Voltage

1.2

///

'"

V .-

22

~

~

W"

FREQUENCY 1Hz!

1.3

~

/

1.1
1.5

0.9
0.7
10·' L-_L-_'---''---''---J
0.0" O.lk
111
10k
lOOk
1M

2A

/

~ 1.3 r-Tj--5~C
>" 1.1

~5

T,ANTALUM

FREQUENCY 1">1

2.3

1.25

100

lOOk

10k

fREQUENCY 1Hz!

10'

....z

-

COUT=25.F
ALlJMINUM

VOUT '" 5V

t--

Output Impedance TO-5
and TO-202 Packages

.~

Tj.25·e

-15V SOLID TANTALUM

JUNCTION TEMPERATURE I'CI

"l!i

10UT'IOomA
.
_ -COUT'I""
VIN - VOUT - 5V -SOLID

~

~

0.990

oS
....

8

our· 5V

T, "25-C
Vou T= -I2V ANDCOUT 'I~F

t;

~

~

100

I

1.005

r

Output Impedance TO-3
and TO-220 Packages

T.=JSrfC
~

- t::::
o TO·3. NO SI~.

1
OJ5

0.5

0.1&

1.0

OUTPUT CURRENT IAI

1.25 1.5

o

25

50

75

100

125

150

AMBIENT TEMPERATURE (ICI

TUH17767-4

'These curves lor LM120.
Derate 25'C lurther lor LM320.

1·51

s::
(0)

N

C)

c

C'I
C')

::e
....

Typical Performance Characteristics

......
c

Maximum Average Power
Dissipation (TO-5)

C'I
..-

::e
....

10.0

Maximum Average Power
DiSSipation (TO-202)
10

TO·&

~
;::

f

§

.

E

INFINITE HEAT SINK

-,........

1.0

I

h
25

50

"o'en

"

WAKEFIELD
HEAT SINK

'.1

I.

1\

207
NO HEAT SINK"/ '
75

100

"-

r\\
125

.....

I

o

I- 2~'t:,J. EAT(SINK

19
17
1&

13

11
9

..... ....
r- ......

AMBIENT TEMPERATURE ('CI

10

20

30

40

sa

60

~

TOol21, &'C
HEAT SINK

'-.. .....

........

a
a

1&0

21

J

HrTSINK

~

I

Maximum Average Power
Dissipation (TO-nO)

I I
INFINITE
I HEA~SINK

J
I

9

E

(Continued)

7a

A'lIBIENT TEMPERATURE ('CI

I
.... }Ool2aIIl"CIW-

i~e:~~~~KSINK
a

25

&II

75

100

12&

150

AMBIENT TEMPERATURE rCI

Short Circuit Current

5

10

15

20 25

3D

35 40

VIN - VOUT (VI
TL/H/n67-5

Typical Applications (Continued)
High Stability 1 Amp Regulator
VOUT (.)

+

01
lM129

C3

_ 11'F

R2**

+

C2tt
_ ll1,uF

RS
10k

R4t

R3**

r-+___....._ - - - - - - - - - . . . . ; ; = - - - V O U T H
TLlH/n67-6
Lead and line regulation -

0.Q1 % temperature stability -

0.2%

tDetermines Zener current.
ttSolid tantalum.
An LM120-12 or LM120-15 may be used to permit higher input voltages, but the regulated output voltage must be at least -15V when USing the LM120-12 and
-lev for the LMI20-15.
"Select resistors to set output voltage. 2 ppm!'C tracl

14

~

16

- - - T' • -55'C'- I - -

18

- - - T:a+25-C -

..

20

-

-

o

-

20

T - .150·C

40

60

LM126 Load Regulation

i
..
;

..."
~
~

~.

I-80

..,.
..
5
~

Z.D

4.0
&.0
1.0
10
12

POt.1iN: ><:? 1<...::
T, '+25'~1" ....
T,' +15D'~......
'. = -5S·C

NE~ .•IEGJ ......

2lI

2.0

I--+--+--=---!-:=,,'--j

~
0;

l.sl--+--+---ho'--+--j

~

~

I.ol--+---h'-+-::;;,.of=----j

~

200

~

100

I--M~7"'~..t"""-.......:--l
40

20

60

LOAD CURRENT

10

z

10
05

!i

l!i
z

20

i

40

80

. 300 l-'I'-ooE"-k:+++-+-+-+-I

~

1.0

~

I-I-t-+-+-+-

INFINITE HEAT SINK

-=

HID

I

;I!FINITE H AT SINK
HID

150

1

~~ ~~~~~I::~

0.10

~ 0.60

.
!
~

!

0.50

15

"

~

gOlD

"-

~~

~

......

0.30

i'
-50 -25 0 25

TA - AMBIENT TEMPERATURE I'C)

'

~ +100

3.0 TA=jZS·C
TA

a ..

:i

I

2.0

..
.~

• SUPPLY

=>

18

20

~V
:/'

22

24

=>

..

~

IL=D
21i

INPUT VOLTAGE ttV)

28

-50 -IS -100 -125

~

0.50

r-..

0.40

DID
0 25 50 15 100 lZ5 150

JUNCTION TEMPERATURE I'CI

LM126
Load Transient Response
.5
Z"

:i"
~

+150

£.1 1 .0 -lOrnA
NEGATiVE REGULATOR

+100

.

+50

~

-50

~

>

./
Til.· -5S·C
TA • +ZS·C
TA s +l2S·C

H-H..-H++H++H-l

~ ~50

us·e

-25

r-..

-50 -Z5

;;

oS

-SUPPLY

-SS'C

~

50 15 100125 ISO

;; ·'50
TA

..~~

LM125
Load Transient Response
for Negative Regulator

4.0

0

AMBIENT TEMPERATURE I·e I

i'

0.60

JUNCTION TEMPERATURE ,'CI

LM125/126
Standby Current Drain

-

1"-

LM125/126 Current Limit Sense
Voltage vs Temperature
for Positive Regulator
~ OBO

0.40

100

'"

~ 090

I'..

'" 0.20
50

TA

_ 0.80

Ii

01
25

-55 -25

LM125/126 Current Limit Sense
Voltage vs Temperature
for Negative Regulator

;

-NoHEATSIN
-OIP'NOHIO

1.0

100

~~~

I

JUNCTION TEMPERATURE '"CI

\ "~

z

50

-50

~

100

10

LM125/126 Maximum Average
Power Dissipation vs
Ambient Temperature

f=ND HEAT

100

~

60

LOAO CURRENT (mAl

1 400 1-1-1--+-+-+-+++-+-1
~

-SS'C

~~

10

1m A)

~ ~~:lpN~~~~~:~:~~~~

,

~

100

80

=>
~

500

LM325/326 Maximum Average
Power Dissipation vs
Ambient Temperature

~

-/ :2

I.S

0.1

i

..
~.

60

0;

..~

r\
~

40

~

LM125/126 Peak Output
Currentvs
Junction Temperature

~

~

T, ..

2.0

LOAD CURRENT ImAI

,......-.,--,---r-'-A

.5

V'

III

1&

2.5

0.5

....... k"

i'v 1' . . . .

~l :::::~I'" V

100

~

..
..
i
i.

V

,..

~

%

25

~

,: •• ,sre' ,.

14

LM125/126 Regulator
Dropout Voltage for
Negative Regulator

ill

~

10...~

LOAD CURRENT 1m AI

~

LM125/126 Regulator
Dropout Voltage for
Positive Regulator

-50

~

=>
"=' -100

-100

3D

TIME 11,../DIVI

TIME'I",/OIVI

TLlH/7776-4

1-65

II

Typical Performance Characteristics
LM125
Load Transient Response
lor Positive Regulator

I

<41

•

+4D

AIL=O-lDmA
POSITIVE REGULATOR

co +Z'

il

-ZO

-10

-ZOO

-60

TIME 12Io/OIVI

LMI26
Line Transient Response
AV IN

II

•

:;

+2QV TO +2lY

+300

TIMEI~IVI

LM125
Line Transient Response
for Negative Regulator

LMI26
Line Transient Response
.. 150

AV" • -ZlV TO -Z3V

IL =10mA

.!.

POSITIVE AEGULATOA

:; +2011

IL =10mA

!ii

.~

..
~
. 'DD
I~

_

+100

I
1

-ZIO

o

40

50

.'

V,. ~1~~5V

114[.

r

~

JD

F"

~

10

POSIT,I~~ AEG~~DR

lao

~

0.1

~

__ c."aJ,
10k

1.0

...

1!!I'___ c. "I~F

I.ak

I_

I

AEGUI~~~O';

;;;

..

P

NEGATIVE.l

&0

..

II

[

-so
-100

TlMEIlIooIOIVI

, LM126
Ripple Rejection

10

1.~IIW'::"~~

ZI

...
~

LM125
Output Impedance
vs Frequency

INI'UT AIPPLE " 10 V...

3D

V

>

TIME IID,.JOIVI

LM125
Ripple Rejection
10

co

S

-ZIO

TlMEIZIo/OIVI

1'1

-50

;:!

~

1

IL =1DmA

'-- NEGATIVE AEGULATOR

w

co

1

"YIN" -15V TO -11V

iz

co +'00

w

~

LI

5 -100

It;

co

TIME II,",OIV)

i

1\

~

e:

•

:1

~

!; --40

I

IL'=1DmA

w

>

..

"YIN" +20V TO +ZlV

:: +lDO

..

co

co

+3DO

S
~ +1110

w

~

:;

;

iIS

.

LM125
Line Transient Response
lor Positive Regulator

LM126
Load Transient Response

!O~i'!A

,,:.

(Continued)

lOOk

0,01 .............IIIII....J..1.1.111.L..===...;;....u
100
10k
\.Ok
lOOk
1M

1M

FAEDUENCY 1Hz!

FREDUENCY IH'I

100

1,Ok

10k

I 10k

\.DM

FIIEDUUCY 1Hz!

LMI26
Output Impedance
Y8 Fraquency
10

~

S

iii!

1.0

!;

0,1

i
..

;

\.Ok

10k
IlOk
FREDUENCY IH,I

\'oM

TLlHI7776-5

1-66

Typical Applications
Basic Regulatorttt

r--r--I

GND---~

i'I "~:; 1-

'Clt..L
I.F

-+.......

C4"

---o-VauT

+VOUT

TL/HI7776-10

tSolid tantalum
ttShori pins 6 and 7 on dip
'Required If regulator Is located an appreciable distance from power supply filter.
"Although no capacitor Is needed for stability, It does help transient response. (If
needed use 1 ,..F electrolytic).

II

1-69

~
~
~

r-------------------------------------------------------------------------------------,

..... ~National
~ semiconductor

::E
....I

~
~

....

::E
....I

LM 133/LM333 3-Ampere Adjustable Negative Regulators
General Description

Features

The LM133/LM333 are adjustable 3-terminal negative voltage regulators capable of supplying in excess of -3.0A
over an output voltage range of -1.2V to -32V. These
regulators are exceptionally easy to apply, requiring only 2
external resistors to set the output voltage and 1 output
capacitor for frequency compensation. The circuit design
has been optimized for excellent regulation and low thermal
transients. Further, the LM133 series features internal current limiting, thermal shutdown and safe-area compensation, making them substantially immune to failure from overloads.
The LM133/LM333 serve a wide variety of applications including local on-card regulation, programmable-output voltage regulation or precision current regulation. The LM1331
LM333 are ideal complements to the LM150/LM350 adjustable positive regulators.

•
•
•
•
•
•
•
•
•
•
•

Connection Diagrams

Output voltage adjustable from -1.2V to -32V
3.0A output current guaranteed, - 55·C to + 150·C
Line regulation typically 0.01 %IV
Load regulation typically 0.2%
Excellent rejection of thermal transients
50 ppml"C temperature coefficient
Temperature-independent current limit
Internal thermal overload protection
P + Product Enhancement tested
Standard 3-lead transistor package
Output is short circuit protected

Typical Applications

TO-3
Metal Can Package

Adjustable Negative Voltage Regulator

CASE IS

+

-VIN

TL/H/9065-1

TO-220
Plastic Package

o

-'IIN-.....--I
TLlH/9065-3

-VOUT

= -1.25V ( 1 + 1::0) + ( -IADJ X R2)

tCl

= 1 f'F solid tantalum or 10 f'F aluminum electrolytic required for stability.

'C2

=

1 f'F solid tantalum is required only if regulator is more than 4' from power supply filter capacitor.

Output capacitors in the range of 1 ""F to 1000 JLF of aluminum or tantalum electrolytic are commonly
used to provide lower output impedance and improved transient response.

TAB IS

t====I- VIN

ADJUST

1 ~F

120

BoHomView
Steel TO-3 Metal Can Package
(KSTEEL)
Order Number LM133K STEEL or
LM333K STEEL
See NS Package Number K02A

+ CIt

C2*

VOUT

YIN
TL/H/9065-2

Front View
3-Lead TO-220 PlastiC Package (T)
Order Number LM333T
See NS Package Number T03B

1-70

Absolute Maximum Ratings

(Note 1)

If Military/Aerospace specified devices are required,

Storage Temperature

please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Power Dissipation
Internally Limited
Input-Output Voltage Differential
35V
Operating Junction Temperature Range
TMIN toTMAX
-55·Cto + 150·C
LM133
-40·Cto + 125·C
LM333

Lead Temperature (Soldering, 10 sec.)
TO-3 Package
TO-220 Package
ESD Susceptibility

-65·Cto

+ 150·C
300·C
260·C
TBD

Electrical Characteristics LM 133

Specifications with standard typeface are for TJ = 25·C, and those with
boldface type apply over the full operating temperature range. (Note 3)
Parameter
Reference Voltage

Conditions

Typical

IL=10mA
3V ,;;: IViN - vourl ,;;: 35V
10mA,;;: IL';;: 3A, P';;: PMAX

Line Regulation
Load Regulation

3V ,;;: IVIN - vourl ,;;: 35V
lour = 50 mA (Note 4)
10 mA ,;;: lour';;: 3A, P ,;;: PMAX
(Notes 4, 5)

Min
(Note 2)

Max
(Note 2)

Units

-1.250

-1.238

-1.262

V

-1.250

-1.225

-1.275

V

0.01

0.02

%N

0.02

0.05

0.2

0.5

0.4

1.0

0.002

0.01

%

Thermal Regulation

10 ms Pulse

Temperature Stability

TMIN ,;;: TJ ,;;: TMAX

0.4

%

Long Term Stability

TJ = 125·C, 1000 Hours

0.15

%

Adjust Pin Current

65

90

70

100

2

6

Adjust Pin Current
Change

10mA,;;: IL';;: 3A
3.0V ,;;: IVIN - vourl ,;;: 35V

Minimum Load
Current

IViN - vourl ,;;: 35V

2.5

5.0

IViN - vourl ,;;: 10V

1.2

2.5

3V ,;;: IViN - vourl ,;;: 10V

3.9

3.0

IVIN - vourl = 20V

2.4

1.25

IViN - vourl = 30V

0.4

0.3

Current Limit
(Note 5)

Output Noise
(% ofVour)

10 Hz to 10 kHz

Ripple Rejection

Thermal Resistance
Junction-to-Case

%/W

p.A
p.A

mA

A

0.003

% (rms)

Your = 10V, f = 120 Hz
CADJ = o p.F
CADJ = 10 p.F

60

dB

TO-3 Package (K STEEL)

1.2

77

Thermal Shutdown
Temperature

163

1-71

150

1.8

·C/W

190

·C

III

Electrical Characteristics LM333 Specifications with standard typeface are for TJ = 25·C, and those with
boldface type apply over the full operating temperature range. (Note 3)
Parameter
Reference Voltage

Conditions
IL=10mA
3V ~ IV,N - vourl ~ 35V
10 mA ~ IL ~ 3A, P ~ PMAX

Line Regulation
Load Regulation
Thermal Regulation

3V ~ IV,N - vourl ~ 35V
lour = 50 mA (Note 4)
10mA ~ IL ~ 3A,P ~ PMAX
(Notes 4 and 5)
10 ms Pulse

Typical

Min
(Note 2)

Max
(Note 2)

-1.250

-1.225

-1.275

-1.250

-1.213

-1.287

V

0.01

0.04

%N

0.02

0.07

0.2

1.0

0.4

1.5

0.002

0.02

Temperature Stability

TMIN ~ TJ ~ TMAX

0.5

Long Term Stability

TJ = 125·C, 1000 Hours

0.2

Adjust Pin Current

%/W

%

65

95

70

100

10 mA ~ IL ~ 3A
3.0V ~ IV,N - vourl ~ 35V

2.5

8

Minimum Load
Current

IV,N - Vour! ~ 35V

2 ••

10

IV,N - vourl ~ 10V

1 ••

..0

Current Limit
(Note 5)

3V ~ IViN - vourl ~ 10V

3.9

IV,N - Vour! = 20V

2.4

1.0

IV,N - Vour! = 30V

0.4

0.20

",A
",A

mA

3.0
A

0.003

% (rms)

Your = 10V, f = 120 Hz
CADJ = O",F
CADJ = 10",F

60

dB

TO·3 Package (K STEEL)

1.2

1.8

3

4

Output Noise
(% ofVour)

10 Hz to 10 kHz

Ripple Rejection

77

TO·220 Package (T)

Thermal Shutdown
Temperature
Thermal Resistance
Junction to Ambient
(No Heatslnk)

%

%

Adjust Pin Current
Change

Thermal Resistance
Junction to Case

Units

163
K Package

35

TPackage

50

·C/W
·C

·C/W

Nol. 1: Absolule Maximum Ra~ngslndlcate limits beyond which damage to the device may oocur. Eleotrlcalspeclflcatlons do not apply when operating the device
outside 01 Its stated operating conditions.
Not. 2: All limits are guaranteed at either room temperature (standard type lace) or at t.mper.ture ••trem•• (bold trP.'.o.) by produotlon testing or
corrslatlon techniques using standard Statistical Ouallty Control (SOC) methods.
Nol. 3: Unle88 otherwise specified: !V,N - VOUT! - 5V, lour = 0.5A, POISS :s: SOW.
Not. 4: Load and line regulation are measured at constant lunctlon temperature, using low duty cycle pulse testing (output voltage changes due to heating effects
are covered by the rhermal Regulation specification). For the rO·3 package, load regulation Is measured on the output pin, '10' below the base of the package.
Nol. &: rhe output current 01 the LMS33Is guaranteed to be " 3A In the range 3V :s: !V,N - Vour! :s: 10V. For the range 10V :s: iVlN - VOUT! :s: 15V. the
guaranteed minimum output current Is equal to: 301 (V,N - VOUT). Reier to graphs lor guaranteed output currents at other voltages.

1·72

Guaranteed Performance Characteristics
LM133 Guaranteed Output Current

5V
(3.0A)

LM333 Guaranteed Output Current

"-

lDV
15V
2DV
25V
3DV
35V
(3.0A) (2.0A) (1.25A) (D.7A) (D.3A) (D.15A)

TESTED TESTED

TESTED

5V
(3.0A)

TESTED TESTED

lOY
15V
2DV
25V
3DV
35V
(3.0A) (2.0A) (l.DA) (D.4A) (D.2A) (D.DBA)

TESTED TESTED

TESTED

(VIN-VOUT)

TESTED TESTED

(VIN-VOUT)
TLlH/9065-4

TLlH/9065-5

Typical Applications (Continued)
- 5.2V Regulator with Electronic Shutdown

TTL
CONTROL-------,
..rON

lN914
787
1%

lN914

+

2N29D7

+

lid'
5.6k-~~'"

249
1%

-8V TO -2DV - - -....- -....- -.......

TLlH/9065-6

Negative Regulator with Protection Diodes

D3'"
MR752OR
SIMILAR

5A. 50Y

'When CL is larger than 20 p.F, 01 protec1s the
LM133 in case the input supply is shorted.
"When C2 is larger than 10 "F and -VOUT is
larger than -25V, 02 protects the LM133 in
case the output is shorted.

·"In case VOUT is shorted to a positive supply.

t-~~--~~------~~----------=~~
- V I N - - -.....- - - - -.....
TL/H/9065-7

1-73

D3 protects the LM133 from overvoltage, and
protects the load from reversed voltage.

•

Typical Applications

(Continued)

High-Performance 9-Ampere Adjustable Regulator
+SENSE

R2

+ C3
lOOpF

VOLTAGE

ADJUST
Ik

+

\lJN

--+-..

-35V-....
(MAX)

I
I
I
I

$

f-____...i\.,.,0.,.,1,.....
•
_ _ _ _-t_-4~---~ =~u:o -28V
@9A**

*
'Wire RI and R4 to the regulator that
provides the highest VOUT with a 3A
load.

0.1

"'Full

output

current

requires

5v,:lvIN-VOUTI':lov. At higher In·
put·output voltages, load current will
be less (see guaranteed curves)
0.1

TL/H/9065-B

Current Regulator

High Stability 10V Regulator

LM329A

287
1%

+
+
I

OUT

Uk
1%

VREF

= R1"

YoUT

........- -.....-

'O.4n ,: RI ,: 120n
TL/H/9065-9

....- - -lOY

15 ppm/'C

-15V --+----'
TL/H/9065-IO

1-74

r-

s::
.....

Typical Applications (Continued)

Co)

Co)
......

High-Current Adjustable Regulator

r-

s::

Co)
Co)
Co)

+SENSE

I

VOLTAGE ADJUST

I

2k

+

+

100 ~F

$

ADJ
VIN
LM333K
0.03
Your
-35V -~~-II-""" VIN CONTROL Your 1'---~~'V\""'-4","""----O -1.2V TO -27V
(MAX)
REGULATOR"
@ 9A··
·Control regulator must have the
est VREF

AOJ

0.03
Your 1----......JIoM_..

t--+--tVIN
LM333K

"Full

output

current

larg~

requires

SV,;IVIN-VOUTI ,;10V. At higher input-output voltages, load current will
be less (see guaranteed curves)

AOJ

0.03
Your t - - - -......JIoM_.

.....---IVIN

LM333K

TL/H/9065-11

Adjustable Lab Voltage Regulator

Adjustable Current Regulator

+25V - - -....._ - -...
r-_-I~~lk

lpF
2k
R1·

lN4002
TL/H/9065-13

lN4002

lOUT

( 1.SV)

= A1

·O.Sfi ,; R1 ,; 24fi

-25V - - -. .- _.......

TL/H/9065-12

'The 10 I'F capacitors are optional to improve ripple reiection.

1-75

.
± 15% adjustable

•

~~----------------------------------------------------~
~
~

:s......
....
:s
~
~

Typical Applications

(Continued)

per watt, within the first 10 ms after a step of power is applied. The lM133's specification is 0.01 %/W, max.

THERMAL REGULATION

When power is dissipate~ in an IC, a temperature gradient
occurs across the IC chip affecting the individual IC circuit
components. With an IC regulator, this gradient can be especially severe since the power dissipation is large. Thermal
regulation is the effect of these temperature gradients on
output voltage (in percentage output change) per watt of
power change in a specified time. Thermal regulation error
is independent of electrical regulation or temperature coefficient, and occurs within 5 ms to 50 ms after a change in
power dissipation. Thermal regulation depends on IC layout
as well as electrical design. The thermal regulation of a voltage regulator is defined as the percentage change of VOUT,

In Figure 1, a typical lM133's output drifts only 2 mV (or
0.02% of VOUT = -10V) when a 20W pulse is applied for
10 ms. This performance is thus well inside the specification
limit of 0,01 %/W x 20W = 0.2% max. When the 20W pulse
is ended, the thermal regulation again shows a 2 mV step as
the lM133 chip cools off. Note that the load regulation error
of about 1 mV (0.01 %) is additional to the thermal regulation
error. In Figure 2, when the 20W pulse is applied for 100 ms,
the output drifts only slightly beyond the drift in the first 10
ms, and the thermal error stays well within 0.1 % (10 mV).

FIGURE 2

FIGURE 1

1-76

~National

~ Semiconductor

LM 137/LM337
3-Terminal Adjustable Negative Regulators
General Description
The LM1371LM337 are adjustable 3-terminal negative voltage regulators capable of supplying in excess of -1.5A
over an output voltage range of -1.2V to -37V. These
regulators are exceptionally easy to apply, requiring only 2
external resistors to set the output voltage and 1 output
capacitor for frequency compensation. The circuit design
has been optimized for excellent regulation and low thermal
transients. Further, the LM 137 series features internal current limiting, thermal shutdown and safe-area compensation, making them virtually blowout-proof against overloads.

•
•
•
•
•
•
•
•

77 dB ripple rejection
Excellent rejection of thermal transients
50 ppml"C temperature coefficient
Temperature-independent current limit
Internal thermal overload protection
P+ Product Enhancement tested
Standard 3-lead transistor package
Output is short circuit protected
LM137 Series Packages and Power Capability

The LM137/LM337 serve a wide variety of applications including local on-card regulation, programmable-output voltage regulation or precision current regulation. The LM137/
LM337 are ideal complements to the LM117/LM317 adjustable positive regulators.

Device

Package

Rated
Power
Dissipation

Design
Load
Current

LM137/337

TO-3(K)
TO-39 (H)

20W
2W

1.5A
0.5A

LM337

TO-220m

15W

1.5A

LM337M

TO-202(P)

7.5W

0.5A

Features
•
•
•
•
•

Output voltage adjustable from -1.2V to -37V
1.5A output current guaranteed, - 55·C to + 150·C
Line regulation typically O.Q1"1oN
Load regulation typically 0.3%
Excellent thermal regulation, 0.002"1o/W

Typical Applications
AdJustable Negative Voltage Regulator

.A

+
;:~C2'

VIN

•

+

;:~Clt

:~ 120n

IADJ
-VIN

~

~2

1 ~F

~

VOUT

LMI371
LM337

-VOUT
TL/H/9067-1

Full output current not available at high Input·output voltages
-VOUT= -1.26V(1

+

':~n)

to,

+ (-IAOJXR2)

= , )£F solid tantalum or , 0 )£F aluminum electrolytic required for stability
'02 = , )£F solid tantalum Is required only If regulator Is more than 4' from power·supply filter capaCitor
Output capaCitors In the range of 1 )£F to 1000 )£F of aluminum or tantalum electrolytic are commonly used 10 provide Improved
output Impedance and relectlon of transients

1-77

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 4)
Power Dissipation
Internally Limited
Input-Output Voltage Differential
40V

Operating Junction Temperature Range
- 55·C to + 150·C
LM137
LM337
O"C to + 125·C
- 65·C to + 150"C
Storage Temperature
300·C
Lead Temperature (Soldering, 10 sec.)
Plastic Package (Soldering, 4 sec.)
260"C
2kVoits
ESDRating

Electrical Characteristics (Note 1)
Parameter

LM137

Conditions
Min

Line Regulation

Tj = 25·C,3V ::;;; iVlN - vOUTI ::;;; 40V
(Note 2) IL = 10 mA

Load Regulation

Tj = 25·C,10 mA::;;; lOUT::;;; IMAX

Thermal Regulation

Tj = 25·C, 10 ms Pulse

LM337

Typ

Max

0.01

0.02

Min

Units

Typ

Max

0.01

0.04

%IV

0.3

0.5

0.3

1.0

%

0.002

0.02

0.003

0.04

%/W

Adjustment Pin Current

65

100

65

100

p,A

Adjustment Pin Current Charge 10 mA::;;; IL::;;; IMAX
3.0V ::;;; IVIN - vOUTI ::;;; 40V,
TA = 25·C

2

5

2

5

p,A

Reference Voltage

Tj = 25·C (Note 3)
3V ::;;; IVIN - vOUTI ::;;; 40V, (Note 3)
10 mA::;;; lOUT::;;; IMAX' P::;;; PMAX

-1.225 -1.250 -1.275 -1.213 -1.250 -1.2B7
-1.200 -1.250 -1.300 -1.200 -1.250 -1.300

Line Regulation

3V ::;;; iVlN - vOUTI ::;;; 40V, (Note 2)

0.02

0.05

0.02

0.07

Load Regulation

10 mA ::;;; lOUT::;;; IMAX, (Note 2)

0.3

1

0.3

1.5

Temperature Stability

TMIN::;;; Tj ::;;; TMAX

0.6

Minimum Load Current

IVIN - vOUTI ::;;; 40V
IVIN - vOUTI ::;;; 10V

2.5
1.2

5
3

Current Limit

IVIN - vOUTI ::;;; 15V
K and T Package
Hand P Package
IVIN - vOUTI = 40V, Tj = 25·C
K and T Package
Hand P Package

1.5
0.5

2.2
O.B

3.5
1.B

0.24
0.15

0.4
0.17

RMS Output Noise, % of VOUT TJ = 25·C,10Hz::;;; f::;;; 10kHz

V
V
%IV
%
%

0.6
2.5
1.5

10
6

mA
mA

1.5
0.5

2.2
O.B

3.7
1.9

A
A

0.15
0.10

0.4
0.17

A
A

0.003

0.003

%

60

60

dB
dB

Ripple Rejection Ratio

VOUT = -10V, f = 120 Hz
CADJ = 10 p,F

Long-Term Stability

Tj = 125·C, 1000 Hours

0.3

1

0.3

1

%

Thermal Resistance,
Junction to Case

H Package
KPackage
TPackage
P Package

12
2.3

15
3

12
2.3
4
7

15
3

·C/W

H Package
KPackage
TPackage
PPackage

140
35

Thermal Resistance,
Junction to Ambient
(No Heat Sink)

66

77

66

77

140
35
50
BO

·C/W
·C/W
·C/W
·C/W
·C/W
·C/W
·C/W

Note 1: Unless otherwise specified. these specifications apply -55'C ,,; TI ,,; + 150'C for the LM137. O'C"; T) ,,; + 125'C for the LM337;VIN - VOUT = 5V; and
lOUT = 0.1 A for the TO-39 and TO·202 packages and lOUT = 0.5A for the T0-3 and TO·220 packages. Although power dissipation is internally limited. these
specifications are applicable for power dissipations of 2W for the T0-39 and TO-202 and 20W for the TO·3 and TO-220. IMAX is 1.5A for the TO-3 and TO-220
packages. and 0.5A for the TO·202 package and 0.2A for the TO-39 package.
Note 2: Regulation is measured at constant junction temperature, using pulse testing with a low duty cycle. Changes in output voltage due to heating effects are

covered under the specification for thermal regulation. Load regulation is measured on the output pin at a point 'I." below the base of the TO-3 and TO-39
packages.
Note 3: Selected devices with tightened tolerance reference voltage available.
Note 4: Refer to RETS137H drawing for LM137H or RETS137K drawing for LM137K military spacifications.

1-7B

Schematic Diagram

r-

.

.,

'J

AD.

"

is:
.....
Co)

......
.....
r-

is:
Co)
Co)

......
YOUT

."
'"

.n

••

...

'51

,.....

..

."."

....

AZZ

.00•

...

..
D2

II

Uk

.."

""sao

....

...""

."
U.

A33

sao

L-----~_4--~_4--4__4~____--------~~------__~~--__~----------_'------------4_0v

.•

TL/H/9067 -2

Thermal Regulation
When power is dissipated in an IC, a temperature gradient
occurs across the IC chip affecting the individual IC circuit
components. With an IC regulator, this gradient can be especially severe since power dissipation is large. Thermal
regulation is the effect of these temperature gradients on
output voltage (in percentage output change) per Watt of
power change in a specified time. Thermal regulation error
is independent of electrical regulation or temperature coefficient, and occurs within 5 ms to 50 ms after a change in
power dissipation. Thermal regulation depends on IC layout
as well as electrical design. The thermal regulation of a voltage regulator is defined as the percentage change of VOUT,
per Watt, within the first 10 ms after a step of power is
applied. The LM137's specification is 0.02%/W, max.

In Figure 1, a typicalLM137's output drifts only 3 mV (or
0.03% of VOUT = -10V) when a 10W pulse is applied for
10 ms. This performance is thus well inside the specification
limit of 0.02%/W x 10W = 0.2% max. When the 10W
pulse is ended, the thermal regulation again shows a 3 mV
step at the LM137 chip cools off. Note that the load regulation error of about 8 mV (0.08%) is additional to the thermal
regulation error. In Figure 2, when the 10W pulse is applied
for 100 ms, the output drifts only slightly beyond the drift in
the first 10 ms, and the thermal error stays well within 0.1 %
(10 mV).

1.
O.IX

1..

T

0.1%

T

\..
0/

r--..
-110m.

\..-100 m.------I

I-

Horizontal sensitivity, 20 ms/div

TL/H/9067 -3

LM137, VOUT = -10V
Y,N - VOUT = -40V
I,L = OA -+ O.2SA -+ OA

TL/H/9067 -4

LM137, VOUT = -10V
Y,N - VOUT = -40V
IL = OA -+ O.2SA ..... OA

FIGURE 2

Vertical sensitivity, 5 mV Idiv

FIGURE 1
1-79

•

Connection Diagrams
TO·3
Metal Can Package

TO·39
Metal Can Package
)-ooot~--

ADJUSTMENT

o--...,.L-- INPUT
Case Is Input

TLIH19067-6

BoHomVlew
Order Number LM137H or LM337H
See NS Package Number H03A

TLIHI9087-6

BoHomVlew
Order Number LM137K STEEL or LM337K STEEL
See NS Package Number K02A
TQ-220
Plastic Package

TO·202
Plastic Package

0

..,

I

I
I

I

f.--

...

I

.. '

\.,

I.. _ _ _ _ _ _ _ _ _ .JI

ADJ-ADJ

--VO UT

VOUT

TLIHI9087-B

Front View

TLIHI90B7-7

Front View

Order Number LM337MP
See NS Package Number P03A

Order Number LM337T
See NS Package Number T03B

1·80

Typical Applications (Continued)
Adjustable Lab Voltage Regulator

- 5.2V Regulator with Electronic Shutdown'
TTL
CONTROL

+ 25V--. .-.....,

....,:=._....__

1.2V TO 20V
lN914

7B7
11\

lN914

249
1%

-BV TO -2DV--...--4.....----'
TUH/9067-10

*Minimum output

~

-1.3V when control input is low

t-'''''"'".-....---I.2V TO -20V

.....-,r:-:-......

Full output current not available
at high input-output voltages

-25V

'The 10 p.F capacitors are optional to improve ripple rejectionTUH/9067_9

Current Regulator

Adjustable Current Regulator

VIN
ICURRENT
,OUTPUT

I

1.250V

OUT~~

·O.ell ,,; AI ,,; 120ll

lOUT

!IOUT

TUH/9067-11

1.5V)
lOUT ~ ( AI ± 15% adiustable
TL/H/9067 -12

Negative Regulator with Protection Diodes

High Stability -10V Regulator
287

1%

+

I p.F

1.5k

1%

~~~~.---e----"--=~f~T

VOUT
~"'--"-"---IOV

L...-r.=..1
-15V-_..._ .....

DI**
IN4002
-VIN-_...____.....

15 ppmrc
TL/H/9067-14

TLlH/9067-13

'When Cl is larger than 20 p.F, 01 protects the LM137 in case the input
supply is shorted
"When C2 is larger than 10 p.F and -VOUT is larger than -25V, 02 protects the LM137 in case the output is shorted

1-81

Typical Performance Characteristics (K Steel and T Packages)

.

~
~

-

-0.2

c

~

~ -0.6

c::

:.'!'I

IL =1.5A

"':' :'3

H ANOP
PACKAGED

-1.2

IDEVrES
0

PACKAGED
DEVICES

....

~
~
....

i -f-

25 50 15 100 125 150

~~

"...

~~

30

10

.
ia

...........

Dropout Voltage

55
50
-15 -50 -25 0 25 50 15 100 125 ISO

40

TEMPERATURE ('CI

Temperature Stability

Minimum Operating Current

1.270

1.8

Ti"-&!~

1.5

C

~ 1.Z60

....
ill

.

~ 1.250

ill
ffi
::t

.
0.5 '--'--'--.l--'--'--'-..l-...!....J
-15 -50-25 0 25 so 15 100125 ISO

.
.;a

;;

il!5

1;
~

j

100

i -f-

;;

r-:C~O)O- i -f-

:!!

CAtJ.F

10

'"

&0
40

ii

1;

0.2

o
25 50 75 100 125 150

~~~
F- ''''r'l
I

o

-

.
~

t
;;;

f= 120 Hz

Ripple Rejection

10

;;

80 r-

ii

50

:!!

50

1;

-10

-20

.

40

1111

40

~

10

100

OUTPUT VOLTAGE (VI

10
'

-I~~

f= 120 Hz

~

"-

IoU

~~

0.6

-'2'

OA

>1=

0.2

..........
....

~~

V

Q

-0.2

I0&oI

-0.4

~~

~i! -0.5

100

Ik

10k

FREOUENCY (Hz)

lOOk

1M

~! -1.0
!!

J

0.01

0.1

~

I

~;

....

== ~

\

o

~

CAD'" 1M

--

~~ 0.4 r0.2

6=

J

fA \ I

-

Load Transient Response
0.&
~

I I

~

20
TIME ,",I

CAD'" lo,.F

0

-0.5

I I I

-- -

:-

B-1.O 30

40

~ -1.&

!::

. \ '-1=0.

0

=

i

'f ~c1""IO i

-0.2
-0.4

5 -0.6

~'OV

r-1VDJT'
r-IL "SOmA
Tj'25'C
I-ICL I.FI I
10

10

OUTPUT CURRENT (AI

I

lICAO' =0

0

!a

CAD'" lo,.F

11-3
10

Tj '25'~1I1I

o

1M

Line Transient Response
0.1

~CAO'"O

lOOk

II

VIN"
VOUT' -IOV

20

FREQUENCY (Hzl

Output Impedance
VIN" -ISV
VOUT = -IOV
IL" 500mA
CL· '~F
Tj"25'C

10k

II

40

l"iDJ"O

t
;;;

20

-40

-30

30

llltWJ

;a

0

o

20

Ripple Rejection
100

Tj " 25'C

o

10

INPUT·DUTPUT DIFFERENTIAL (VI

;a

VIN-VOUT·5V
IL"SOOmA

20

0.4

f-

TEMPERATURE ('CI

Ripple Rejection

:!!

''''Tj"25'C

0.8
0.&

"
1.230
-75 -50 -25 0

.Pl

1.0

ill

1.240

~

1.2

~
....

r--

TEMPERATURE (,CI

100

1.4

.!

..~

, ..,..

&0

INPUT·OUTPUT DIFFERENTIAL (VI

3.5 r::'~...-;:r.-""""'''''T'"'T'"'''

~

&5

c

-

20

10

TEMPERATURE I'CI

"

15

.3

\..

VIN" -15V
VOUT' -IOV

-1.4
-15 -50 -25

C

T~;;-- j" 150'C

~

\

5; -1.0

.S

-'-'-~'-55'C

I! 'O!5A r-

-0.8

>

-'

Adjustment Current
10

--T'-Z5°C

r--./....

-0.4

:!

Current Limit

Load Regulation

0.2

VIIN"

~I5J

-il

'"

r- VOUT" -IOV

~

INL· SOmA

~"25'C

II

f'jF I
10

20

30

40

TIME ""I
TL/H/9067 - I 5

1·82

~National

~ Semiconductor

LM 137HVILM337HV 3-Terminal Adjustable Negative
Regulators (High Voltage)
General Description

Features

The LM137HV/LM337HV are adjustable 3-terminal negative voltage regulators capable of supplying in excess of
-1.5A over an output voltage range of -1.2V to -47V.
These regulators are exceptionally easy to apply, requiring
only 2 external resistors to set the output voltage and 1
output capacitor for frequency compensation. The circuit
design has been optimized for excellent regulation and low
thermal transients. Further, the LM137HV series features
internal current limiting, thermal shutdown and safe-area
compensation, making them virtually blowout-proof against
overloads.

•
•
•
•
•
•
•
•
•
•
•
•
•

The LM137HV/LM337HV serve a wide variety of applications including local on-card regulation, programmable-output voltage regulation or precision current regulation. The
LM137HV/LM337HV are ideal complements to the
LM117HVILM317HV adjustable positive regulators.

Output voltage adjustable from -1.2V to -47V
1.5A output current guaranteed, -55'C to + 150'C
Line regulation typically 0,01 %/v
Load regulation typically 0.3%
Excellent thermal regulation, 0.002%/W
77 dB ripple rejection
Excellent rejection of thermal transients
50 ppml'C temperature coefficient
Temperature-independent current limit
Internal thermal overload protection
P+ Product Enhancement tested
Standard 3-lead transistor package
Output short circuit protected

Typical Applications
Adjustable Negative Voltage Regulator

_

_

...........
V..;,;IN'i

-VIN

LMI37HV/
LM337HV

LV.,;;O;,:U,;"T._ _ _....I - _

r-

-VOUT
TL/H/9066-1

tel

~

'C2

= 1 p.F solid tantalum is required only 11 regulator is

I p.F solid tantalum or 10 p.F aluminum electroly1ic
required for stability. Output capacitors in the
range of I p.F to 1000 p.F of aluminum or tantalum
electroly1ic are commonly used to provide im·
proved output impedance and rejection of tran~

sients.
more than 4" from power·supply filter capacitor.

1-83

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 3)
Power Dissipation
Internally limited
Input-Output Voltage Differential
50V

Operating Junction Temperature Range'
-55'C to + 150"C
LM137HV
LM337HV
O"Cto +125'C
Storage Temperature
-65'C to + 150'C
Lead Temperature (Soldering, 10 sec.)
300"
ESD rating is to be determined.

Electrical Characteristics (Note 1)
Parameter

LM337HV

LM137HV

Conditions
Min

Line Regulation

TJ = 25'C, 3V s; IVIN-Vourl S; 50V,
(Note 2) IL = 10 mA

Load Regulation

TJ = 25'C, 10 mA S; lour S; IMAX

Thermal Regulation

TJ = 25'C, 10 ms Pulse

Typ

Max

0.01

0.02

Min

Units

Typ

Max

0.01

0.04

%N

0.3

0.5

0.3

1.0

0/0

0.002

0.02

0.003

0.04

%/W

Adjustment Pin Current

65

100

65

100

p.A

Adjustment Pin Current Change 10 mA S; IL S; IMAX
3.0V S; iVlN - vourl S; 50V,
TJ = 25'

2

5

2

5

p.A

4

6

3

6

p.A

Reference Voltage

TJ = 25'C, (Note 3)
3V S; IVIN-Vourl S; 50V, (Note 3)
10 mA S; lour S; IMAX, PS; PMAX

-1.225 -1.250 -1.275 -1.213 -1.250 -1.287
-1.200 -1.250 -1.300 -1.200 -1.250 -1.300

Line Regulation

3V S; iVlN-Vourl S; 50V, (Note 2)
IL = 10 mA

0.02

0.05

0.02

0.07

%N

1

0.3

1.5

%

Load Regulation

10 mA S; lour S; IMAX, (Note 2)

0.3

Temperature Stability

TMIN S; Tj S; TMAX

0.6

Minimum Load Current

IVIN-Vourl S; 50V
IVIN-Vourl S; 10V

2.5
1.2

5
3

Current Limit

IVIN-Vourl S; 13V
KPackage
H Package
IVIN-Vourl = 50V
K Package
H Package

1.5
0.5

2.2
0.8

3.2
1.6

0.2
0.1

0.4
0.17

0.8
0.5

RMS Output Noise, % of Your TJ = 25'C,10 Hz S; f S; 10 kHz
Ripple Rejection Ratio

Your = -10V, f = 120 Hz
CADJ = 10 p.F

0.6
10
6

mA
mA

1.5
0.5

2.2
0.8

3.5
1.8

A
A

0.1
0.050

0.4
0.17

0.8
0.5

A
A

60

77

%

2.5
1.5

0.003
66

V
V

66

0.003

%

60

dB
dB

77

Long-Term Stability

TA = 125'C, 1000 Hours

0.3

1

0.3

1

%

Thermal Resistance, Junction
to Case

H Package
KPackage

12
2.3

15
3

12
2.3

15
3

'C/W
'C/W

140
140
'C/W
Thermal Resistance, Junction H Package
'C/W
to Ambient
KPackage
35
35
Note 1: Unless otherwise specified. these specmcatlons apply: -SS'C ,,; TJ ,,; +ISO'C for the LM137HV, O'C ,,; Tj ,,; +12S'C for the LM337HV; VIN-VOUT =
SV; and lOUT = O.IA for the T0-39 package and lOUT = O.SA for the T0-3 package. Although power dissipation is Internally limited, these specifications are
applicable for power dissipations of 2W for the TO·39 and 20W for the TO·3, IMAX Is I.SA for the T0-3 package and O.2A for the TO-3S package.
Note 2: Regulation is measured at constant junction temperature, using pulse testing with a low duly cycle. Changes In output voltage due to heating efiects are
covered under the specification for thermal regulations, Load regulation is measured on the output pin at a point %" below the base of the TO·3 and TO-39
packages.

Note 3: Refer to RETSI37HVH drawing for LMI37HVH or RETSI37HVK for LMI37HVK military specifications.

1-84

R]

60

OAOJ

·Nv

•

'

R2

•

• 2k

CD

3=.
m
04

()

------r----~~:-~~lr~~~~=t~~t,-l~~~]'~r-·t:'---'r I
,

,

' ,

en
()
=r

,

C

iii'

co

OVOUT

Dl

Cl

25pF

3

RIZ
ZZD

RZl
100

a,
U'I

RZ6
lZI

RZ5
lID

RZ4
15k

Rl6
O.Z
Rl5
10

R16

600
Rl4

-+--......

R18 ...
4.21

150

OlO
Rll
0.04

RZO
41
RlD

Rll
500

SOO
,

,

,

,

. , '

,

"

,

,

OVIN
TUH/9066-2

AHl££W1'AHl£~W1

Thermal Regulation
In Figure 1, a typical LM137HV's output drifts only 3 mV (or
0.03% of Your = -10V) when a 10W pulse is applied for
10 ms. This performance is thus well inside the specification
limit of 0.02%/W x 10W = 0.2% max. When the 10W pulse
is ended, the thermal regulation again shows a 3 mV step as
the LM137HV chip cools off. Note that the load regulation
error of about 8 mV (0.08%) is additional to the thermal
regulation error. In Figure 2, when the 10W pulse is applied
for 100 ms, the output drifts only slightly beyond the drift in
the first 10 ms, and the thermal error stays well within 0.1 %
(10 mY).

When power is dissipated in an IC, a temperature gradient
occurs across the IC chip affecting the individual IC circuit
components. With an IC regulator, this gradient can be especially severe since power dissipation is large. Thermal
regulation is the effect of these temperature gradients on
output voltage (in percentage output change) per Watt of
power change in a specified time. Thermal regulation error
is independent of electrical regulation or temperature coefficient, and occurs within 5 ms to 50 ms after a change in
power dissipation. Thermal regulation depends on IC layout
as well as electrical design. The thermal regulation of a voltage regulator is defined as the percentage change of Vour,
per Watt, within the first 10 ms after a step of power is
applied. The LM137HV's specification is 0.02%/W, max.

t

t

0.1% 1--I-1f~=~~~=l-----+-I-+---1

0.1% f---+--f--4---II--+--I-+---I-+--l

L~-*~~~~ffi*~ffiffi
V

--I

10ms

L~~~~~~ffi*~ffiffi

I-

1---100 m s - - l
TL/H/9066-3

LMI37HV. VOUT

~

TUH/9066-4

-lOY

LMI37HV. VOUT

VIN-VOUT ~ -40V
IL

VIN-VOUT

~ OA~0.25A~OA

IL

~

~

-lOY

-40V

~ OA~0.25A~OA

Horizontal sensitivity. 20 ms/div

Vertical sensitivity. 5 mVldiv

FIGURE 2

FIGURE 1

Connection Diagram (See Physical Dimensions section for further information)
TO·3

T0-39

Metal Can Package

Metal Can Package
~........-

ADJUSTMENT

0--7'"-- INPUT
CASE IS INPUT
TLIH/9066-6

Bottom View

TUH/9066-5

Order Number LM137HVH or LML337HVH
See NS Package Number H03A

Bottom View
Order Number LM137HVK Steel or LM337HVK Steel
See NS Package Number K02A

1·86

Typical Applications (Continued)
Adjustable High Voltage Regulator
+50V--+--.,
t-=~"'-"--1.2V TO +47V

1-"..;;.;....- . .- - -1.2V TO -47V
-50V--. .-

.......
TL/H/9066-7

Full output current not available
at high input·output voltages
"The 10 p.F capacitors are optional to improve ripple rejection

Current Regulator

Adjustable Current Regulator

hf

lOUT

ICURRENT
,OUTPUT

= VREF
Rl

Rl

1

• O.BIl ,;: Rl ,;: 12011

lOUT

lOUT

1.5V)
= ( R1

.
±15% adlustable

TL/H/9066-8
TL/H/8066-9

Negative Regulator with Protection Diodes

High Stability -40V Regulator
5.23k*
1%

+
1 "f

1.5k*

D2**
lN4002

1%

Your

1:;-4,...--&--+-- -40V

~:::.:r::..:..JJ~"'-""--"'--:::~fVUT

35 ppmr C

L-..."".........

Dl**
lN4002

-46V-"",",~--'

TL/H/9066-11

----....I

-VIN-_....

• Use resistors with good tracking TC
TUH/9066-10

'When CL is larger than 20 f'F, 01 protects the
lM137HV in case the input supply is shorted
"When C2is larger than 10 f'F and -VouTis larger than
-25V, 02 protects the lM137HV is case the output is
shorted

1-87

< 25 ppm/'C

> ,-----------------------------------------------------------------------,
::J:
I"'Typical Performance Characteristics (H and K-STEEL Package)
M
~
Current Limit
Adjustment Current
0.2 Load Regulation
....I

:>::J:
....
:&
I"'M

....I

3

i:i

j:

c

-t-

-0.2

.=-0.'

l"-

~ -0.4

~

-0.8

~

-1.0

;

-1.2

.

... ~

N....

PACKAGED t-IDEVICES

IL ·1.5A

\

:0

~ACKAa~

o
0

25 50 75 100 125 150

DEVICES

o

TEMPERATURE I'C)

l""-

~~,

~~

VIN'-IIV
V?UT' -IOV

-1.4
-75 -50 -2&

80

~

-= 25'1:
-55'C
1q---'-r:
- - I = I5D"C

11 'Ol5A -

ro

~ ~~
~~

~

H

2&

50
-75 -50 -25 0 IS 50 75 100 125 150

50

INPUT·OUTPUT DIFFERENTIAL IV)

1,170

TEMPERATURE I'C)

Temperature Stability

Minimum Operating Current
3

~ 1.260

..e
;
~

0,5 .......I-.l-.l-.J....J...-'-..L....L.....J
-7& -50 -25 0 2& 50 7& 100 11& 110

.....

Ripple Rejection

.
..~

i

Ripple Rejection

CAL"lo. F

......

60
40

I

10

o

- -

....;;C~D)O- -

-

-

o

80 t-

iD

.'"

60

~

V,N-VOUT'IV
'L o 500mA
'-120 H.
Tj'2&'C

iii

-10

-30

40

i

40

20

iii

20

~

10

-40

OUTPUT VOLTAGE IV)

100

lk

10k

lOOk

-I~D

VIN'
VOUT' -IOV

f= 120 Hz

TI'25'~1I1I

o

1M

0,01

.
....
i~
.""

-02

.....

-OA

I I

0,6

~z

J\CADJ'O

:OJ: 02

.=

!~
~

!:

5!
!!~

0

-0.&

·CADJ·,o.F

- -IVOJT=~'0V

--

1:1

~

-1.0
30

CAOJoO

I

1
1

'L CAOJ = lo.F

1 1 1

- V~N" ~I&J
o -10V
,... r- VOUT

-rl

'"

C -D.' : -

:=
a

20

ff \T

.\~

0

"" -OA

•

IICLjMI

TIME "',)

f-

== i: -0.2

r-'L =IOmA
Tj'25'C

10

0,6

61
~i

11\

ilL\ I

10

Load Transient Response

.

!~ 0.4
0.2

I
I.

I I

0,4

0,1
OUTPUT CURRENT IA)

Line Transient Response
0.8

lljtJIU;

l~iOJ'O

FREQUENCV 1Hz)

!~

50

IIII II

60

0
-10

40

Ripple Rejection

z

co

3D

20

100

80

.
i

iD

:a

10

INPUT·OUTPUT OIFFERENTIAL IV)

100

80

co

o

TEMPERATURE I'C)

~~

I,;~

Iro

1.230
-71 -50 -II 0 2& 50 71 100 125 110

TEMPERATURE I'C)

TI"25 C ~
TjOII:;j

t- 1 - -

1.240

100

TjloJs.,~,

-f--

~ 1.2&0

co

....

.... ~

I'-.

40

0
-0.6
-1.0

=
~

-1.5

-

INL - 50 mA
Tj=I&'C

~ l'!J
10

20

J
I
30

40

TIME",,)

Tl/H/90SB-12

1-88

r-

...

s::
w
CD
.....
rs::
w

~National

~ Semiconductor

w

LM138, LM338
5-Amp Adjustable Regulators

CD

General Description
The LM138 series of adjustable 3-terminal positive voltage
regulators is capable of supplying in excess of 5A over a
1.2V to 32V output range. They are exceptionally easy to
use and require only 2 resistors to set the output voltage.
Careful circuit design has resulted in outstanding load and
line regulation-comparable to many commercial power
supplies. The LM138 family is supplied in a standard 3-lead
transistor package.
A unique feature of the LM138 family is time-dependent current limiting. The current limit circuitry allows peak currents
of up to 12A to be drawn from the regulator for short periods
of time. This allows the LM138 to be used with heavy transient loads and speeds start-up under full-load conditions.
Under sustained loading conditions, the current limit decreases to a safe value protecting the regulator. Also included on the chip are thermal overload protection and safe
area protection for the power transistor. Overload protection
remains functional even if the adjustment pin is accidentally
disconnected.
Normally, no capacitors are needed unless the device is
situated more than 6 inches from the input filter capacitors
in which case an input bypass is needed. An output capacitor can be added to improve transient response, while bypassing the adjustment pin will increase the regulator's ripple rejection.

the regulator is "floating" and sees only the input-to-output
differential voltage, supplies of several hundred volts can be
regulated as long as the maximum input to output differential is not exceeded, i.e., do not short-circuit output to
ground. The part numbers in the LM138 series which have a
K suffix are packaged in a standard Steel TO-3 package,
while those with a T suffix are packaged in a TO-22D plastic
package. The LM 138 is rated for - 55°C :0; TJ :0; + 15DoC,
and the LM338 is rated for DOC :0; TJ :0; + 125°C.

Features
•
•
•
•
•
•
•

Guaranteed 7 A peak output current
Guaranteed 5A output current
Adjustable output down to 1.2V
Guaranteed thermal regulation
Current limit constant with temperature
P+ Product Enhancement tested
Output is short-circuit protected

Applications
• Adjustable power supplies
• Constant current regulators
• Battery chargers

Besides replacing fixed regulators or discrete designs, the
LM138 is useful in a wide variety of other applications. Since

Connection Diagrams (See Physical Dimension section for further information)
(TO-3 STEEL)
Metal Can Package

(TO-220)
Plastic Package
VOUT

J-

lol ~

:~:UT
AOJ

Front View
Order Number LM338T
See NS Package Number T03B
TLIH/9060-30

Bottom View
Order Number LM1381< STEEL or LM3381< STEEL
See NS Package Number K02A

1-89

TL/H/9060-31

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 4)
Power Dissipation

Lead Temperature
Metal Package (Soldering, 10 seconds)
Plastic Package (Soldering, 4 seconds)

300'C
260'C
TBD

ESD Tolerance

Internally limited

Input/Output Voltage Differential
Storage Temperature

Operating Temperature Range

+40V, -0.3V

LM138
LM338

-65'C to + 150'C

-55'C s: TJ s: +150'C
O'C s: TJ s: + 12S'C

Electrical Characteristics
Specifications with standard type face are for TJ = 2S'C, and those with boldface type apply over full Operating Temperature Range. Unless otherwise specified, VIN - VOUT = SV; and lOUT = 10 mA. (Note 2)
Symbol

Parameter

LM138

Conditions
Min

VREF

Reference Voltage

VRLOAD

Line Regulation

3V

s:

(VIN - VOUT)

s:

Load Regulation

10 mA

Thermal Regulation

20ms Pulse

V

lOUT

s:

SV (Note 3)

Adjustment Pin Current

~IADJ

Adjustment Pin Current Change

10 mA s: lOUT s: SA,
3V s: (VIN - VOUT) s: 3SV

~VR/T

Temperature Stability

TMIN

ILOAD(Min)

Minimum Load Current

VIN - VOUT = 3SV

ICL

Current Limit

VIN - VOUT s: 10V
DC
O.S ms Peak

s: TJ

1.19

s: 3SV (Note 3)

IADJ

1.24

1.29
0.Q1

%/V

0.02

0.04

%N

0.1

0.3

%

0.3

0.6

%

0.002

0.Q1

%/W

45

100

/'oA

0.2

5

/'oA

5

mA

3.5
5
7

V

0.005

1

s: TMAX

%

8

A
A

12

VIN - VOUT = 30V

1
0.003

%

60
75

dB
dB

VN

RMS Output Noise, % of VOUT

10HzS:fs: 10kHz

~VR

Ripple Rejection Ratio

VOUT = 10V, f = 120 Hz, CADJ = O/'oF
VOUT = 10V, f = 120 Hz, CADJ = 10/'oF

~VIN

Units
Max

lOUT = 10 mA, TJ = 2S'C
3V s: (VIN - VOUT) s: 3SV,
10 mA s: lOUT s: SA, P s: SOW

VRLlNE

Typ

Long-Term Stability

TJ = 12S'C, 1000 Hrs

8JC

Thermal Resistance,
Junction to Case

KPackage

8JA

Thermal Resistance, junction to
Ambient (No Heat Sink)

KPackage

60

0.3

3S

1-90

1

A

1

%

1

'C/W
'C/W

Electrical Characteristics (Continued)
Specifications with standard type face are for TJ = 25'C, and those with boldface type apply over full Operating Tempera·
ture Range. Unless otherwise specified, VIN - VOUT = 5V; and lOUT = 10 mA. (Note 2)
Symbol

Parameter

LM338

Conditions
Min

Reference Voltage

VREF

lOUT

Line Regulation

V

10 mA ,;; lOUT';; 5V (Note 3)

Thermal Regulation

20 ms Pulse

IADJ

Adjustment Pin Current

alADJ

Adjustment Pin Current Change

10 mA ,;; lOUT';; 5A,
3V ,;; (VIN - VOUT) ,;; 35V

aVRIT

Temperature Stability

TMIN ,;; TJ ,;; TMAX

ILOAD(Min)

Minimum Load Current

VIN - VOUT

ICL

Current Limit

VIN - VOUT';; 10V
DC
0.5 msPeak

RMS Output Noise, % of VOUT

VN
AVR

Ripple Rejection Ratio

aVIN

1.19

3V ,;; (VIN - VOUT) ,;; 35V (Note 3)

Load Regulation

VRLOAD

5
7

TJ

K Package
TPackage

6JA

Thermal Resistance, Junction to
Ambient (No Heat Sink)

K Package
TPackage

0.03

%/V

0.06

%/V

0.1

0.5

%

0.3

1

%

0.002

0.02

%/W

45

100

/J- A

0,2

5

/J- A

10

mA

%

A
A

8

12

60

V

0.005

1

= 125'C, 1000 hrs

Long-Term Stability
Thermal Resistance
Junction to Case

1.29

0.02

3.5

= 10V, f = 120 Hz, CADJ = O/J-F
= 10V, f = 120 Hz, CADJ = 10 /J-F

6JC

1.24

1

= 35V

VIN - VOUT = 30V
10Hz,;;f,;; 10kHz
VOUT
VOUT

Units
Max

= 10 mA, TJ = 25'C

3V,;; (VIN - VOUT) ,;; 35V,
10 mA,;; lOUT';; 5A, p,;; 50W
VRLlNE

Typ

A

0.003

%

60
75

dB
dB

0.3

1

%

1

'C/W
'C/W

4
35
50

'C/W
'C/W

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics.

Note 2: These specifications are applicable for power dissipations up to SOW for the TO·3 (K) package and 2SW for the TO·220 rn package. Power dissipation is
guaranteed at these values up to 15V input-output differential. Above 15V differential, power dissipation will be limited by internal protection circuitry. All limits (i.e.,

the numbers in the Min. and Max. columns) are guaranteed to National's AOQL (Average Outgoing Quality Level).
Note 3: Regulation is measured at a constant junction temperature, using pulse testing with a low duty cycle. Changes in output voltage due to heating effects are
covered under the specifications for thermal regulation.

Note 4: Refer to RETS13BK drawing for mil~ary specifications of LM13BK.

Typical Performance Characteristics

5....

c;

=
~....

~

Current Limit
14
PRELOAD ~~itffi 0
12 ~
TCAimUI C
.....
10

-

8
8

Current Limit

r12

VIN~VDUT 'IsV

~\~VD~~

....
2

VIN-VDUT" 3DV
1111111

10

1.0
TlMElm.1

1111111

188

B

I

I

4

0

: : : ~~CKu~~:~NL1~:~'T
_ TCASE'2SoC

PR~LDAr·tt:::

lfo

~DUT"IDV

I'

4

0
0.1

18

~ .\

3:1

~ PRELOAD'
I I
~ PRELDAD' sA-

"

I

I

~PIREL~AD

iI lA

~'h.j

1'1-1
0

20
3D
40
10
INPUT·DUTPUT DIFFERENTtAL IVI

14
12

Current Limit

r:MrrIAD'~1I1111
II
./ PRELOAD' lA

5....
10 PRELOA'~~
~ 8
~ 8 PRtL~A~~I~A

~

IUIIIII

4
Y,N 'IDV
2 VDUT'5V
TCASE ',~,~:C
0
10
0.1
1
TtMEIIIIIl

tOO
TLIH/9060-4

1-91

Typical Performance Characteristics
Load Regulation

au

~

r- DllJ -

-0.1

.... ....
~

.....

vour- 1OV

:

~

1.240

......

~

~

/'"

w

~ 1.230

--

g:

I-

'

100

1--t---t--""""'"--"IL......,j

~

50

..

~

i

~ii!

20

o

10-3

I-""~"""~'---+--+--l

10

10

,

100

"

10,

101No

o

1M

,.z

.ti

8D

:;J

80

I

II:
ii!

.'"

,.
a;

40

1'-

20
VIR" 15V
Vm~

IIV

T....
35

~

Irc

50

w

.....

II:
ii!

100

"

10'

100'

1M

0.1

Load Transient Response

---k' , , , '\

---

C~'O;HJ·d~

C~- 0; lAW' 0

-IT'

Ir

""
~~

!!'"

1.0

o.s

.J\.
CL = 1 /-IF; CADJ" lD /.IF

V,N"5V
V r-r- VOUY#
IOV

Vour - 18V
-1.0 lOUT ""
T, = H'C
~_ -1.5

~=

PRELOAD" 100 mA

TCASE" 25',

I LI

J I I

L

J I I
10

10
OUTPUT CURRENT (AI

3

~L • \ "F1 CL ~ 10 ~F

&0_

N.

V,N
VOUT"0V
f= 120 Hl
TCASE' 25 C

50

FREOUENCY (H.,

I I I

j'-..... CADJ' 0

"~V

~

Line Transient Response
-

flit

! - bl..L
40

10

OUTPUT VOL lAGE IVI

1.5

40

30

I lillli
r-.... CAOJ"10"F

70

--21

30

20

;;

F-- CAOJ-~

lour" 2A

I
25

10

~:26~C
I

Ripple Rejection

,"" "C~OJ -10"F

0:

w

.... Ti· 25"C

80

iii

20

""

::,.,;:;

~

INPUT·OUTPUT DIFFERENTIAL (VI

Ripple Rejection

J"F

15

o

FREQUENCY IH.)

~

5

Ti' -55"C

100

VI.-VJJ
IDIIJ - 2A
I-121Hz
T,- Z5'C

a

Minimum Operating
Current

10-5 L..,.........Jt--.......Jt--.......L"":";:;"'_-'

I I

40

75 50 -25 a 25 50 75 100 125 150

t;
"'0~ 1--4!--"""","--4

CAO~.

...

30

~

Ripple Rejection

i

/

35

TEMPERATURE rc)

,....."":"r--i---,--,--,

TEMPERATURE ('C)

I-

I

I

"~ 10-2 1-"""","---.'1'--74

1.210
-75 -50 -25 0 25 50 75 100 125 150

10

/1'

~ ......

~ 1~1 1--1---1-~t--~~-4

~

100

./

Output Impedance
'0

V

~ 1.220

~

40

C;

TEMPERATURE I'CI

w

45

"

TEMPERATURE rCI

~1.Z50

~

!i;

--

1
-75 -50 -25 0 25 50 75 100 125 150

Temperature Stability

50

ill

-75 -50 -25 0 25 50 75 100 125 150

-0.4

1.261

."

-~

V,N-15V

PRELOAO - 50 mA

IGIR = SA

...

.3

,.,

-I- ~-3A

iii

t;

I!: -1J.3

""

;;:

1A

~ '1

55

..\VOUT -100 mV

-

0.1

§\! -0.2

Adjustment
Current

Dropout Voltage
4

II
=
; r- ~-~
~
!!

(Continued)

20

30

I J\I I
IIUl
10

40

TIME loll

I

20

30

40

TIME(psl

TLlH/9060-5

1-92

Load Regulation
The LM138 is capable of providing extremely good load regulation but a few precautions are needed to obtain maximum performance. The current set resistor connected between the adjustment terminal and the output terminal (usually 2400) should be tied directly to the output of the regulator (case) rather than near the load. This eliminates line
drops from appearing effectively in series with the reference
and degrading regulation. For example, a 15V regulator with
0.05n resistance between the regulator and load will have a
load regulation due to line resistance of 0.05n x IL. If the
set resistor is connected near the load the effective line
resistance will be 0.05n (1 + R2/R1) or in this case, 11.5
times worse.
Figure 2 shows the effect of resistance between the regulator and 240n set resistor.

Application Hints
In operation, the LM138 develops a nominal 1.25V reference voltage, VREF, between the output and adjustment terminal. The reference voltage is impressed across program
resistor R 1 and, since the voltage is constant, a constant
current 11 then flows through the output set resistor R2, giving an output voltage of

Your = VREF (1 +

:~) + IADJR2.

LM338

1

VOUT

LM338
-'

VIN

RS

VOUTr
.....IV\"""'...-VOUT

AOJ

I

RI*
:

120

TLiH/9060-6

FIGURE 1
Since the 50 p.A current from the adjustment terminal represents an error term, the LM138 was designed to minimize
IADJ and make it very constant with line and load changes.
To do this, all quiescent operating current is returned to the
output establishing a minimum load current requirement. If
there is insufficient load on the output, the output will rise.

TL/H/9060-7

FIGURE 2. Regulator with Line
Resistance In Output Lead
With the TO-3 package, it is easy to minimize the resistance
from the case to the set resistor, by using 2 separate leads
to the case. The ground of R2 can be returned near the
ground of the load to provide remote ground senSing and
improve load regulation.

External Capacitors
An input bypass capacitor is recommended. A 0.1 p.F disc
or 1 p.F solid tantalum on the input is suitable input bypassing for almost all applications. The device is more sensitive
to the absence of input bypassiing when adjustment or output capacitors are used but the above values will eliminate
the possiblity of problems.
The adjustment terminal can be bypassed to ground on the
LM138 to improve ripple rejection. This bypass capacitor
prevents ripple from being amplified as the output voltage is
increased. With a 10 p.F bypass capacitor 75 dB ripple rejection is obtainable at any output level. Increases over
20 p.F do not appreciably improve the ripple rejection at
frequencies above 120 Hz. If the bypass capacitor is used, it
is sometimes necessary to include protection diodes to prevent the capacitor from discharging through internal low current paths and damaging the device.
In general, the best type of capacitors to use are solid tantalum. Solid tantalum capacitors have low impedance even at
high frequencies. Depending upon capacitor construction, it
takes about 25 ~F in aluminum electrolytic to equal 1 ~F
solid tantalum at high frequencies. Ceramic capacitors are
also good at high frequencies; but some types have a large
decrease in capacitance at frequencies around 0.5 MHz.
For this reason, 0.01 ~F disc may seem to work better than
a 0.1 ~F disc as a bypass.

Protection Diodes
When external capacitors are used with any IC regulator it is
sometimes necessary to add protection diodes to prevent
the capacitors from discharging through low current pOints
into the regulator. Most 20 ~F capacitors have low enough
internal series resistance to deliver 20A spikes when shorted. Although the surge is short, there is enough energy to
damage parts of the IC.
When an output capaCitor is connected to a regulator and
the input is shorted, the output capacitor will discharge into
the output of the regulator. The discharge current depends
on the value of the capaCitor, the output voltage of the regulator, and the rate of decrease of VIN. In the LM138 this
discharge path is through a large junction that is able to
sustain 25A surge with no problem. This is not true of other
types of positive regulators. For output capacitors of 100 p.F
or less at output of 15V or less, there is no need to use
diodes.
The bypass capacitor on the adjustment terminal can discharge through a low current junction. Discharge occurs
when either the input or output is shorted. Internal to the
LM138 is a 50n resistor which limits the peak discharge
current. No protection is needed for output voltages of 25V
or less and 10 ~F capacitance. Figure 3 shows an LM138
with protection diodes included for use with outputs greater
than 25V and high values of output capaCitance.

Although the LM138 is stable with no output capacitors, like
any feedback circuit, certain values of external capacitance
can cause excessive ringing. This occurs with values between 500 pF and 5000 pF. A 1 ~F solid tantalum (or 25 ~F
aluminum electrolytic) on the output swamps this effect and
Insures stability.

1-93

III

co
C")
C")

~

r---------------------------------------------------------------------------------,
Application Hints (Continued)

«;

DI
IN4II02

C")

.....

:=l

1-4,...-....--...

-VOUT

RZ

TLiH/9060-8
01 protects against CI
02 protects against C2

VOUT

~ 1.25V (I + *) + IADJR2

FIGURE 3. Regulator with Protection Diodes

Typical Applications
Regulator and Voltage Reference

Temperature Controller

~. . .- - - - - -. .-

VOUT

Rl

1.2k

HEATER

TUH/9060-3
TUH/9060-IO

Full output current not available
at high input-output voltages

1.2V-25V Adjustable Regulator

tOpiional--improves transient response. Output capacitors in the range of
I /IF to 1000 /IF of aluminum or tantalum electrolytic are commonly used
to provide improved output impedance and rejection of transients.
'Needed if device Is more than 6 Inches1rom filter capacitors.
ttVOUT
"RI

~

~ 1.25V ( I

+

*) +

IADJ (R2)

2400 for LM138. RI, R2 as an assembly can be ordered from

Bourns:
MIL part no. 7105A-AT2-502
COMM part no. 71 05A-AT7-502

1-94

en

()

:::T
CD

3

a5"
o

I

I~:o I~!n IR~_ I lIn.

~

R4

RII

i"
co

11

VIN

iiJ

3

~RIZ

5.Bk ~ 7Z

RZ6
0.03

l4I1'
BV

b

~
son

b &

RZ5
3

VOUT
AOJ
TUH/9060-9

8&&W'/8&~W'

II

Q)
C")
C")

::&
....

r------------------------------------------------------------------------------------------,
Typical Applications (Continued)
Precision Power Regulator with Low Temperature Coefficient

~
.....

::&
....

1---..- - - - - - -...-

VOUT ~4V

Uk

Rl
375

TL/H/9060-12

'Adjust for 3.75 across AI

Slow Turn-On 15V Regulator

Adjustable Regulator with Improved Ripple Rejection

Dl*
lN4DD2

TL/H/9060-14
TL/H/S060-13

tSolid tantalum
'Discharges Cl if output is shorted to ground
"AI = 2400 for LM138

High Stability 10V Regulator

Digitally Selected Outputs

r:e-...--t'---To.............---4~r~Jlr

~----+- vDur

VIN------f

Rl

2k
5%

Cl

~D.l"'F

R2

1.5k
1%
LM329B

INPUTS

TL/H/9060-1S

TL/H/9060-16

"'Sets maximum VOUT
"AI = 2400 for LM138

1-96

r-----------------------------------------------------------------------------'r
Typical Applications

a:
-"

(Continued)

w

~
r

15A Regulator

a:
w

R5

0.1

w

0)

R4
2k

Rl
0.05

R6

0.1

VIN -"'~N\r-. .- - -. .--t

R2

0.1
~--------~--~---VOUT*

+

Cl
10"F

C2
2Z"F

'Minimum load-IOO mA

TL/H/9060-17

oto 22V Regulator

5V Logic Regulator with Electronic Shutdown"

VOUT
5V

VIN 7V-35V

C2

O.I,.F

III

TTL
lk

··Minimum output:::::: 1.2V

TUH/9060-1 B

Light Controller
-IOV
TUH/9060-19

'AI = 2400. A2 = 5k for LMI38
Full output current not available
at high input-output voltages

TL/H/9060-11

1-97

Typical Applications (Continued)
12V Battery Charger
600

R6
0.2

VIN :'18V

+

TO 12V
BATTERY

Rl
3k

O.I,..F

+

TLIHI9060-20

Adjustable Current Regulator

Precision Current Limiter

TUHI9060-22

Tracking Preregulator
R2
720

R3
12.0

Your

V-5VTO -10V
TUHI9060-21

5A Current Regulator
OUTPUT
ADJUST

TLIHIS060-24

TLIHIS060-23

1-98

Typical Applications

(Continued)

AdJusting Multiple On·Card Regulators with Single Control·

I-. . . .-VOUT

vlN

tMinlmum load-l0 mA
'All oulputs wilhin

± 100 mV
TL/H/B060-25

Power Amplifier

~-------4~--------------------~--"--35V
lOOk

Av~ l,RF~ 10k,CF~

Av

~

10, RF

~

lOOk, CF

100pF
~

10 pF

Bandwidlh :;, 100 kHz
TL/H/B060-27

Distortion ,;; 0.1 %

Simple 12V Battery Charger

TL/H/B060-28

'Rs-seta oulpul impedance of charger loUT

~ Rs ( 1 + *)

Use of Rs allows low charging rales with fully charged battery.
"The 1000 I'F Is recommended to filler oul inpul transients

1·99

Typical Applications (Continued)
Adjustable 15A Regulator

Current Limited 6V Charger

VIN _ _. ._-I

VIN
9V TO JOV
Z40

+
'UOOpf"
1.1k

t-t-""i'Y~~- 4.5V TO Z5V

O.Z·
5k
TL/H/9060-29

"Set

max charge current to 3A

"The '000 fLF Is recommended to filter out input transients.

5k

TLlH/9060-26

10A Regulator
R
0.1

R

D.'

VIN

-"-..J\N~-"'---""---I

Cl
1"",

DUTPUT*
..........-'.2V TO ZOV

+

'Minimum load-'OO mA
TL/H/9060-2

1-100

~National

~ Semiconductor

LM 140A/LM 140/LM340A/LM340/LM7800/LM7800C
Series 3-Terminal Positive Regulators
General Description

Features

The LM140AlLM140/LM340AlLM340/LM7800/LM7800C
monolithic 3-terminal positive voltage regulators employ internal current-limiting, thermal shutdown and safe-area
compensation, making them essentially indestructible. If adequate heat sinking is provided, they can deliver over 1.0A
output current. They are intended as fixed voltage regulators in a wide range of applications including local (on-card)
regulation for elimination of noise and distribution problems
associated with single-point regulation. In addition to use as
fixed voltage regulators, these devices can be used with
external components to obtain adjustable output voltages
and currents.

• Complete specifications at 1A load
• Output voltage tolerances of ±2% at Tj = 25'C and
±4% over the temperature range (LM140AlLM340A)
• Line regulation of 0.01% of VourlV of AV,N at 1A load
(LM140AlLM340A)
• Load regulation of 0.3% of Vour/A (LM140AlLM340A)
• Internal thermal overload protection
• Internal short-circuit current limit
• Output transistor safe area protection
• P+ Product Enhancement tested

Device

Considerable effort was expended to make the entire series
of regulators easy to use and minimize the number of external components. It is not necessary to bypass the output,
although this does improve transient response. Input bypassing is needed only if the regulator is located far from
the filter capacitor of the power supply.
The entire series of regulators is available in the steel TO-3
power package. The LM340AlLM340/LM7800/LM7800C
series is also available in the TO-220 plastic power package.

Output Voltages

Packages

LM140AlLM140 5,12,15

TO-3(K)

LM340AlLM340 5,12,15

TO-3 (K), TO-220 (T)

LM7800

8,18,24

TO-3 (K), TO-220 (T)

LM7800C

5,6,8,12,15,
18,24

TO-3 (K), TO-220 In

-------------------------------------------------------------------Typical Applications
Fixed Output Regulator
INPUT

T

T

Cl • ....l-

O.22"F

,
,LM340.XX

OUTPUT
F --

T

Current Regulator

Adjustable Output Regulator

,1--T
l

INPUT'
'::;:';~--II

GND....l-

C2*·

~--+--.-I

T
- ' - CI

LM340·5.0

I,t----1.-.-.OUTPUT

I

.;;IN:;.P;;.;UT+_-'li

I

Rl

j--Rl

o.2Z "F

O22
' "F

-

OUTPUT

lOUT

TL/H/77Bl-l

TUH/77BI-3

'Required if the regulator Is located far from the
power supply filter.
"Although no output capaCitor Is needed for sta·
bllity, It does help transient response. (If need·
ed, use 0.1 "F, ceramic disc).

LM340.XX

~CI'L..-"""-'"

~
TL/HI77BI-2
VOUT = 5V + (5V/RI + '0) R2 5V/RI > 3 '0.
load regulation (lor) :::: [(RI + R2)/RIJ (lor of
LM340·5).

1-101

lOUT

= V2-3 + 10

 4.990

"'>


~!2

1.5 :;;:

=
....
=

....
"
I!:

"
o

iii

.....=

>

20 <

::I

~

0.5 ~
z

!:j
10 ".

....

TIME (5 msJolV)

~

~
TIME (5 m,IOIV)
TL/H/77BI-5

:i
...I

~

~2

1A, TA

2:

...I

.....
o

..

=

~

2:

C')

...I

140AK-5.0, lOUT

o

.....
o

:i

LIne Regulation

140AK-5.0, VIN = 10V, TA = 25°C

~

...I

(Continued)

S
T1./HI77Bl-B

Equivalent Schematic

r..,..----t---------1t---......--.,..VIN
RI
10k

1112

RIB
0.25

'-----+---+-+-0 VOUT
RlO

01

R21
2.67k

L....~--6----~---6--_4__~~~~--+-~----~GND

TL/HI77BI-7

1-108

r-----------------------------------------------------------------------------~

Application Hints
The LM340/LM7BXX series is designed with thermal protection, output short-circuit protection and output transistor
safe area protection. However, as with any Ie regulator, it
becomes necessary to take precautions to assure that the
regulator is not inadvertently damaged. The following describes possible misapplications and methods to prevent
damage to the regulator.
Shorting the Regulator Input: When using large capacitors at the output of these regulators, a protection diode
connected input to output (Figure 1) may be required if the
input is shorted to ground. Without the protection diode, an
input short will cause the input to rapidly approach ground
potential, while the output remains near the initial Vour because of the stored charge in the large output capacitor.
The capacitor will then discharge through a large internal
input to output diode and parasitic transistors. If the energy
released by the capacitor is large enough, this diode, low
current metal and the regulator will be destroyed. The fast
diode in Figure 1 will shunt most of the capacitors discharge
current around the regulator. Generally no protection diode
is required for values of output capacitance ~ 10 /-LF.

Raising the Output Voltage above the Input Voltage:
Since the output of the device does not sink current, forcing
the output high can cause damage to internal low current
paths in a manner similar to that just described in the
"Shorting the Regulator Input" section.
Regulator Floating Ground (Figure 2): When the ground
pin alone becomes disconnected, the output approaches
the unregulated input, causing possible damage to other circuits connected to Vour. If ground is reconnected with power "ON", damage may also occur to the regulator. This fault
is most likely to occur when plugging in regulators or modules with on card regulators into powered up sockets. Power
should be turned off first, thermal limit ceases operating, or
ground should be connected first if power must be left on.
Transient Voltages: If transients exceed the maximum rated input voltage of the device, or reach more than O.BV
below ground and have sufficient energy, they will damage
the regulator. The solution is to use a large input capacitor,
a series input breakdown diode, a choke, a transient suppressor or a combination of these.

I~

--t:

VIN-+--. . .

1

11

340

VIN

I

I

340

I

"""
~
......

~

:s::
.o
"""

"~

:s::
o
"""
!:
:s::
~
:s::
.....
Co)

~

Co)

~

co

o
~

~

:s::
.....
co
o
o

o

II

J { J

: I - - + _ VOUT

~

:s::
.-

VOUT

TLlH/77Bl-9

FIGURE 2. Regulator Floating Ground
TL/H/77Bl-B

FIGURE 1. Input Short

VIN-. . .-

340

.....:

•

VOUT

T
I

..L.

""
I
I

~

TL/H/77Bl-l0

FIGURE 3. Transients

1-109

Typical Applications
Fixed Output Regulator

High Input Voltage Circuits

t--p---vo

v l - - -....--I

t--p----vo
0.1 pF

(NOTE 1)

TL/H/7781-14

TL/H/7781-13

Note 1: Bypass capaCitors are recommended for optimum stability and transient response, and should be located as close as possible to the regulator.

I -.....-Vo
0.1 pF

TL/H/7781-15

High Current Voltage Regulator
01
I
VI _ ...._ _-\:2N6'3,3_ _ _ _...;;;;;Q;;;'=.;......_ _ _--,

Rl
3.011

11(01);"

t--p-.....~
---:;- Vo

lOMax
IREGMax

0.1 pF

Rl = ~ =
IREG

,6(Ql)VBE!QIl
IREG Max (,6

+

1)

10 Max

TUH/7781-16

High Output Current, Short Circuit Protected

lise
IN -

.......- -..........,."f'r-.......,

t--+-,...- OUT
RSC

Rl
3.011

= 0.8
Isc

RI

=

0.1 pF

,6VBE!QIl
IREG Max (,6

+

1)

10 Max

TL/HI7781-17

Positive and Negative Regulator
t-~'""""--""'-- + OUT

L-~---_~---6_--~~---DUT

TLlH17781-18

1-110

,-----------------------------------------------------------------------.r
s:::
....

Connection Diagrams and Ordering Information

~

TO-3 Metal Can Package (K and KC)

!i:
....

TO-220 Power Package (T)

~
r

s:::
Co)

TUH17781-11

0l:Io

Bottom View
Steel Package Order Numbers:
LM140AK-5.0
LM140AK-12
LM140AK-15
LM140K-5.0
LM140K-12
LM140K-15
LM140AK-5.0/883 LM140AK-12/883 LM140AK-15/883
LM140K-5.0/883 LM140K-12/883 LM140K-15/883
LM340AK-5.0
LM340AK-12
LM340AK-15
LM340K-5.0
LM340K-12
LM340K-15
LM7806CK
LM7808CK
LM7808K
LM7818CK
LM7818K
LM7824CK
LM7824K
See Package Number K02A

TL/H17781-12

Top View
Plastic Package Order Numbers:
LM340AT-5.0 LM340T-5.0
LM340AT-12 LM340T-12
LM340AT-15 LM340T-15
LM7812CT
LM7805CT
LM7806CT
LM7815CT
LM7808CT
LM7818CT
LM7824CT
See Package Number T03B

~r

s:::
Co)
0l:Io

~

r

s:::
~

C)

~

r

s:::
....,
CD

C)
C)

Aluminum Package Order Numbers:
LM340KC-5.0
LM340KC-12
LM340KC-15
LM7805CK
LM7812CK
LM7815CK
See Package Number KC02A

o

TO-39 Metal Can Package (H)

TUH/7781-19

Top View
Metal Can Order Numberst:
LM140H-5.0/883
LM140H-6.0/883
LM140H-8.0/883
LM140H-12/883
LM140H-15/883
LM140H-24/883
See Package Number H03A
tThe specifications for the LM140H/883 devices are not contained in this datasheellf specifications for these devices
are required, contact the National Semiconductor Sales Office/Distributors.

1-111

.J
Q

;

:l

r--------------------------------------------------------------------------------,

~National

~ Semiconductor

Q

"III'

i.J LM 140L/LM340L Series 3-Terminal Positive Regulators
General Description
The LM 140L series of three terminal positive regulators is
available with several fixed output voltages making them
useful in a wide range of applications. The LM140LA is an
improved version of the LM78LXX series with a tighter output voltage tolerance (specified over the full military temperature range), higher ripple rejection, better regulation and
lower quiescent current. The LM140LA regulators have
±2% VOUT specification, 0.04'Yo/V line regulation, and
0.01 %/mA load regulation. When used as a zener diode/resistor combination replacement, the LM140LA usually results in an effective output impedance improvement of two
orders of magnitude, and lower quiescent current. These
regulators can provide local on card regulation, eliminating
the distribution problems associated with single point regulation. The voltages available allow the LM140LA to be used
in logic systems, instrumentation, Hi-Fi, and other solid state
electronic eqUipment. Although designed primarily as fixed
voltage regulators, these devices can be used with external
components to obtain adjustable voltages and currents.
The LM140LA/LM340LA are available in the low profile
metal three lead TO-39 (H) and the LM340LA are also available in the plastic TO-92 (Z). With adequate heat sinking the
regulator can deliver 100 mA output current. Current limiting
is included to limit the peak output current to a safe value.
Safe area protection for the output transistor Is provided to
limit internal power dissipation. If internal power dissipation

becomes too high for the heat sinking provided, the thermal
shut-down circuit takes over, preventing the IC from overheating.
For applications requiring other voltages, see LM117L Data
Sheet.

Features
• Line regulation of 0.04'Yo/V
• Load regulation of 0.01 'Yo/mA
• Output voltage tolerances of ±2% at Tj = 25°C and
±4% over the temperature range (LM140LA)
± 3 % over the temperature range (LM340LA)
• Output current of 100 mA
• Internal thermal overload protection
• Output transistor safe area protection
• Internal short circuit current limit
• Available in metal TO-39 low profile package
(LM140LA/LM340LA) and plastiC TO-92 (LM340LA)

Output Voltage Options
LM140LA-5.0
LM140LA-12
LM140LA-15

5V
12V
15V

LM340LA-5.0
LM340LA-12
LM340LA-15

5V
12V
15V

Connection Diagrams
TO-39 Metal Can Package (H)

GND

(CASE)

INPUT

TUHI77B2-2

Bottom View
Order Number LM140LAH-5.0, LM140LAH-5.0/883, LM140LAH-12,
LM140LAH-12/883, LM140LAH-15, LM140LAH-15/883, LM340LAH-5.0, LM340LAH-12 or LM340LAH-15
See NS Package Number H03A
TO-92 Plastic Package (Z)
OUTPUT

INPUT

TLlHI77B2-3

Bottom View

Order Number LM340LAZ-5.0, LM340LAZ-12 or LM340LAZ-15
See NS Package Number Z03A
1-112

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 4)

Operating Temperature Range
LM140LA
LM340LA

Input Voltage

Storage Temperature Range
Metal Can (H package)
Molded TO·92

Maximum Junction Temperature

35V

Internal Power Dissipation (Note 1)

- 55'C to + 125'C
O'Cto +70'C

Internally limited

+ 150'C
- 65'C to + 150'C
- 55'C to + 150'C

Lead Temperature (Soldering, 10 sec.)
Metal Can
Plastic TO·92

+300'C
+ 230'C

Electrical Characteristics
Test conditions unless otherwise specified. TA = -55'C to + 125'C (LM140LA), TA = O'C to +70'C (LM340LA),10 = 40 mA,
CIN = 0.33 p.F, Co = 0.01 p.F.
Output Voltage Option

S.OV

Input Voltage (unless otherwise noted)
Symbol
Va

Parameter
Tj = 25'C

Output Voltage
Over Temp.
(Note 3)

LM140LA

line Regulation

4.9

Tj = 25'C

10 = 1 -100mAor
10= 1-40mAand
VIN = ()V

4.85

Load Regulation Tj = 25'C

VN
aVIN

11.5

Tj = 25'C
Tj = 125'C

Quiescent
Current Change

Tj = 25'C

12.25

14.7

12.5

14.4

12

30

15.3
15.6
V

15.45

(17.5-30)
65

37

(14.2-30)

70

(17.3-30)

30

65

37

(14.5-30)

(7.5-25)

15

12.35 14.55

30

30

Units

ITyp I Max

(17.6-30)

(14.3-27)

18

70

20

10

40

12

50

20

40

30

80

35

100

24
4.5

3

4.2

mV
1000 hrs

30
4.5

3.1

4.2

4.5

aLoad 10 = 1 - 40 mA

0.1

0.1

0.1

0.5

0.5

0.5

Ripple Rejection f = 120 Hz, VIN = ()V

55

(7.5-25)

(14.3-30)

(17.5-30)

40

80

90

62
(7.5-18)

Tj = 25'C, 10 = 40 mA

7

47

54
(14.5-25)

14.2

mA

4.2

aline
VIN = ()V
Tj = 25'C (Note 2)
f = 10 Hz-10 kHz

mV

(17.5-30)

5

3

aVOUT
Input Voltage
Required to
Maintain line
Regulation

Min

5.15 11.65

(7-25)

10 = 1 - 40mA
10 = 1 - 100mA

23V

ITyp I Max

(14.5-27)

12

Quiescent
Current

Output Noise
Voltage

11.75

18

10=40mA
VIN = ()V

Long Term
Stability

ala

5.1
5.2

(7-20)

10 = 100 mA
VIN = ()V

10

5

4.8

Min

(7.2-20)
LM340LA

aVo

Min Typ Max

10 = 1 - 100mA

1SV

19V

10V

I I

Conditions

Output Voltage

12V

45

52

mA

p.V

dB

(17.5-28.5)

17.3

V

Note 1: Thermal resistance of H·package Is typically 2S'C/W BiC, 2SO"C/W BIA still air, and 94'C/W BjA 400 If/min of air. For the Z·package is SO'C/W BIC, 232'CI
W BIA still air, and SS'C/W BjA at 400 If/min of air. The maximum junction temperature shall not exceed 12S'C on electrical parameters.
Note 2: It is recommended that a minimum load capacitor of 0.01 f'F be used to limit the high frequency noise bandwidth.
Note 3: The temperature coefficient of VOUT is typically w~hin 0.Q1 % VoI'C.
Note 4: A military RETS specification is available upon request. At the time of printing, the LMI40LA·S.O, ·12, and ·15 RETS specifications complied with the Min
and Max IIm~s In this table. The LMI40LAH·5.0, LMI40LAH·12. and LM140LAH·15 may also be procured as Standard Military Drawings.

1-113

Typical Performance Characteristics
Maximum Average
Power Dissipation
(Metal Can Package)

Maximum Average Power
Dissipation
10

--

i

"

i
co
a:

II!

f

10

10

1.0

5.0

LM140LAH

6.0
co

Maximum Average Power
Dissipation (Plastic Package)

2.0

INFINITE HEAT SINK

V" ........ .......

l-

1.0

WITH 30"CIW HEAT SINK....;

0.5

.

r-..

'"

NO HEATSINK- ~

0.2
0.1
-71 -50 -25

1=

f

f

~

.
iii.

i

i

1.0

0:

0.1

~

a:

~

WITH 30"CIW HEAT SINK

25

50

1.0
0.1

0.1
0

7& 100 125

15

30

45

7&

60

1 300 I
iB20D fI
~

..
5

TI"

~15'C

r-....

TI" 21'C

r--... :".......

Ti-IIO'C

j"'--.

i : r-+-t--t-I--f"~o..±=t

:s

5

10

f-+--+-+-+--+-+--+-I

I;

~
~

_

15

20

25

..

1.0

~

0.5

co

25 50

10

i....

aD

co

~

60

ill
0:

...a:
~

40

1l
....

~

a:

Ul

i

Vn • 'OV
VOUT =5V
IOUT"4O mA

;;

"

11 -25'C

10k

lk

lOOk

1M

3.3

LMI40LA-I.0
VIN .. ,OV

..s....

3.2
3.1

IL "4DmA

1l
....

a:
a:

3.0
2.9
2,8

;;

2.7
2.6

;0

i5

2.B
2.4

lOOk

Quiescent Current

3.B
3.1
3,4
3.2
3.0
2.&

10k

3.4

i

I

II

VolIT "5V
lOUT .,4DmA
TJ-Z&-C

Z2

"

2.0
lk

100

FREQUENCV 1Hz!

Quiescent Current

ii

100

./
0.1

75 100 125

4.0

10

lOUT" 40 mA

JUNCTION TEMPERATURE I'CI

Ripple Rejection

o

76

TA - 21'C
Cor::J
COUT =I.F TANTALUM'

~

!

0.5

-75 -50 -25 0

30

100

20

80

w

Z

1.0

INPUT·OUTPUT DIFFERENTIAL IVI

..

45

V'N -10V
VOUT" 5V

1.0

"C

o ~L-L-~~~~-L~
o

3D

Output Impedance

!i!

o

15

10
~VOUT-l00mV

jl

100

o

AMBIENT TEMPERATURE I'CI

Peak Output Current

r---

I

I

AMBIENT TEMPERATURE rCI

AMBIENT TEMPERATURE I"CI

400

0,4" LEAD LENGTH
FROM PC BDARD
0.121" LEAD LENGTH
FREE AIR
FRDM PC lOARD
FREE AIR

2
0.1

0

0.125" LEAO LENGTH
FROM PC BOARD
WITH 72"CIW HEAT SINK

co
1=

iii
CI

LM34DLAZ

5

FREQUENCV 1Hz)

10

II

20

25

30

"

.......

""

2.5
2.4
-75 -50 -25

INPUT VOLTAGE IVI

0

25

50

I"'--,

"

75 tOO t25

JUNCTION TEMPERATURE rCI
TUH/7782-4

Typical Applications
Fixed Output Regulator
INPUT--4"'~

Adjustable Output Regulator

~~"'-OUTPUT

INPUT

--"-=i

t--,,-+--OUTPUT

TL/H/7782-5

'Required if the regulator is localed far from lhe power supply filler.

*·See note 3 in the electrical characteristics table.
VOUT = SV
SVlRl

1-114

=

+

(SVlRl

+

TL/H/7782-6

10) R2

3 10 load regulation (L.) [(RI

+

R2)/Rl) (L. of LMI40LA-S.O)

Equivalent Circuit

,--"1----r-------------------.,..--...,..-----......-

THERMAL
SHUTDOWN

~ -4.8

.

:;

l-

-4.7

lit
1 1
1 1

-4.4
-4.2

10M

-50
OUTPUT CURRENT (AMPSI

f - FREOUENCY IHII

1M

-5.1
~ -5.0

/1 ....--:
TI =25 C

10Il10

-5A
-5.3

1
1

+ ""'po'L""""

10k

Output Voltage vs
Temperature

TI = -WC

1.2

Ik

f - FREOUENCY (H.I

V

1.&

8
>

a.DI
100

100

TI =+15I1"C

1.8

0.&
10

126

Minimum Input·Output
Voltage Differential

E
,lOUT '100 mA
~
V'N"'-tOV
TI =25'C

lID

T. - AMBIENTTEMPERATURE rCI

Output Impedance
10

76

50

100

150

T - TEMPERATURE rCI

TL/HI778S-4

Typical Applications (Continued)
----~----~.-----~-----------t~----~------------------~e_---vouT(·1
Dl

+ C3
_

LM129A

I~F

R2'

C1 ...•
4.7~F

+

SOLID

TANTALUM

VIN - VOUT ~ 3V

R3*

LM145

~~-------4~--------------------~~----~~~T~~'2V
TUH/778S-S

'Select resistors to set output voltage. 1 ppm/C tracking suggested.
"Cl Is not needed

npower supply filter capacitor is within 3'

of regulator.

tOetermlnes zener current May be adjusted to minimize temperature drift.
ttSolid tantalum.
Load and line regulation
Temperature drift

<

0.01 %

< 0.001 %/C

1-118

Typical Applications (Continued)
High Stability Regulator
5V ,;; V+ ,;; 25V
(UNREGULATED)

C2

0.047 "F
01
lN457

C3
200 pF

+

-15V';; VIN';; -4.5V

0-.....-4
TLlH/7785-6
"C1 is not needed if power supply filter capacitor is within 3 11 of regulator.
tKeep C4 within 2" of LM345.

"02 sets initial output voltage accuracy. The LM113 is available in -5, -2, and -1 % tolerance.

-2V EeL Termination Regulator
Dual 3 Amp Trimmed Supply

+ INPUT ()-;~

Variable Output (-5.DVto -15V)

LMtZl

+5.oV

RI
CI

1~F

SOL 10
TANTALUM

110

+

=;::

2.~F

+

lk

=~s·

+C2
4.1.F

+

SOLID
TANTALUM

4 l~F
OLIO
TANTALUM

R2

SOLID
TANTALUM

220

22
tNPUT

0-"'--4

1--"'---.-0

OUTPUT

COM

2.~

F_..:!:.

OLIO

·Optional. Improves transient
response and ripple rejection.

lk

TANTALUM

-INPUT ()-; .....

--=~ ANTALUM

330

SOL 10_r-

TL/H/7785-8

_':'4. 7~F

~ 22

LM145-5

-5.oV

TL1H17785-7

1-119

R1 + R2)
VOUT= -5V ( ~

C)

In

r----------------------------------------------------------------------------,

~ ~National

~ ~ semiconductor
In

~ LM150, LM350A/LM350
~ 3-Amp Adjustable Regulators
..-

~

General Description
The LM150 series of adjustable 3-terminal positive voltage
regulators is capable of supplying in excess of 3A over a
1.2V to 33V output range. They are exceptionally easy to
use and require only 2 external resistors to set the output
voltage. Further, both line and load regulation are comparable to discrete designs. Also, the LM150 is packaged in
standard transistor packages which are easily mounted and
handled.
In addition to higher performance than fixed regulators, the
LM 150 series offers full overload protection available only in
IC's. Included on the chip are current limit, thermal overload
protection and safe area protection. All overload protection
circuitry remains fully functional even if the adjustment terminal is accidentally disconnected.
Normally, no capacitors are needed unless the device is
situated more than 6 Inches from the input filter capacitors
In which case an input bypass is needed. An output capacitor can be added to improve transient response, while bypassing the adjustment pin will increase the regulator's ripple rejection.
Besides replacing fixed regulators or discrete designs, the
LM150 is useful in a wide variety of other applications. Since
the regulator is "floating" and sees only the input-to-output
differential voltage, supplies of several hundred volts can be
regulated as long as the maximum input to output differential is not exceeded, i.e., avoid short-circuiting the output.
By connecting a fixed resistor between the adjustment pin
and output, the LM150 can be used as a precision current
regulator. Supplies with electronic shutdown can be
achieved by clamping the adjustment terminal to ground

which programs the output to 1.2V where most loads draw
little current.
The part numbers in the LM150 series which have a K suffix
are packaged in a standard Steel TO-3 package, while
those with a T suffix are packaged in a TO-220 plastic package. The LM150 is rated for -55'C ~ TJ ~ + 150'C, while
the LM350A is rated for -40'C ~ TJ ~ + 125'C, and the
LM350 is rated for O'C ~ TJ ~ + 125'C.

Features
•
•
•
•
•
•

•
•
•
•

Adjustable output down to 1.2V
Guaranteed 3A output current
Guaranteed thermal regulation
Output Is short circuit protected
Current limit constant with temperature
P+ Product Enhancement tested
86 dB ripple rejection
Guaranteed 1 % output voltage tolerance (LM350A)
Guaranteed max. 0.01 %IV line regulation (LM350A)
Guaranteed max. 0.3% load regulation (LM350A)

Applications
• Adjustable power supplies
• Constant current regulators
• Battery chargers

Connection Diagrams
(TO·3 STEEL)
Metal Can Package

(TO·220)
Plastic Package
VOUT

J.

Case Is Output

TL/H/S061-5

Front View
TL/H/9061-4

Order Number LM350AT or LM350T
See NS Package Number T03B

Bottom View

Order Number LM150K STEEL,
LM350AK STEEL or LM350K STEEL
See NS Package Number K02A

1-120

r
il:
.....

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 4)
Power Dissipation
Input-Output Voltage Differential
Storage Temperature

U1

Lead Temperature
Metal Package (Soldering, 10 sec.)
Plastic Package (Soldering, 4 sec.)

300'C
260'C
TBD

ESD Tolerance

Internally Limited

Operating Temperature Range
LM150
LM350A
LM350

+35V
-65'C to + 150'C

-55'C,;; TJ';; +150'C
-40'C';; TJ';; +125'C
O'C,;; TJ';; +125'C

Electrical Characteristics
Specifications with standard type face are for TJ = 25'C, and those with boldface type apply over full Operating Tempera·
ture Range. Unless otherwise specified, VIN - Your = 5V, and lour = 10 mA. (Note 2)
Parameter

LM150

Conditions

Reference Voltage

3V ,;; (VIN - Your) ,;; 35V,
10 mA ,;; lour';; 3A, P ,;; 30W

Line Regulation

3V ,;; (VIN - Your) ,;; 35V (Note 3)

Load Regulation

10 mA ,;; lour';; 3A (Note 3)

Thermal Regulation

20 ms Pulse

Units

Min

Typ

Max

1.20

1.25

1.30

V

0.005

0.01

%IV

0.02

0.05

%IV

0.1

0.3

%

Adjustment Pin Current

0.3

1

%

0.002

0.01

%/W

50

100

",A

0.2

5

",A

5

mA

Adjustment Pin Current Change

10 mA ,;; lour';; 3A,3V ,;; (VIN - Your) ,;; 35V

Temperature Stability

TMIN ,;; TJ ,;; TMAX

1

Minimum Load Current

VIN - Your = 35V

3.5

Current Limit

VIN - Vour';; 10V
VIN - Your = 30V

3.0

4.5

0.3

1

%

A
A

RMS Output Noise, % of Your

10Hz,;;f,;; 10kHz

Ripple Rejection Ratio

VOUT = 10V, f = 120 Hz, CADJ = 0 ",F

Long-Term Stability

TJ = 125'C, 1000hrs

0.3

1

%

Thermal ReSistance, Junction
to Case

K Package

1.2

1.5

'C/W

Thermal Resistance, Junction
to Ambient (No Heat Sink)

K Package

35

Your = 10V, f = 120 Hz, CADJ = 10 ",F

1-121

66

0.001

%

65

dB

86

dB

'C/W

o
......

r
il:

Co)

U1

o

!:
r
il:
Co)
U1

o

Electrical Characteristics (Continued)
Specifications with standard type face are for TJ = 25'C, and those with boldface type apply over full Operating Temperature Range. Unless otherwise specified, VIN - Your = 5V, and lour = 10 mAo (Note 2) (Continued)
Parameter
Reference Voltage

LM350A

Conditions
lour

= 10 mA, TJ = 25'C

3V ,,;; (VIN - Your) ,,;; 35V,
10 mA ,,;; lour";; 3A, P ,,;; 30W
Line Regulation

Load Regulation

Thermal Regulation

LM350

Min

Typ

Max

1.238

1.250

1.262

Min

Typ

Units
Max
V

1.225 1.250 1.270 1.20 1.25 1.30

3V ,,;; (VIN - Your) ,,;; 35V (Note 3)

10 mA ,,;; lour";; 3A (Note 3)

0.005

0.01

0.005 0.03 %IV

0.02

0.05

0.02 0.07 %IV

0.1

0.3

0.1

0.5

%

0.3

1

0.3

1.5

%

0.002 0.03 %/W

0.002

0.01

Adjustment Pin Current

50

100

50

100

/LA

Adjustment Pin Current Change 10 mA,,;; lour";; 3A,3V";; (VIN - Your) ,,;; 35V

0.2

5

0.2

5

/LA

10

mA

Temperature Stability

20 ms Pulse

V

1

TMIN ,,;; TJ ,,;; TMAX

= 35V

Minimum Load Current

VIN - Your

Current Limit

VIN - Your ,,;; 10V
VIN - Your = 30V

3.5

Ripple Rejection Ratio

Your
Your

Long-Term Stability

TJ

Thermal ReSistance, Junction
to Case
Thermal Resistance, Junction
to Ambient (No Heat Sink)

= 10V, f = 120 Hz, CADJ = O/LF
= 10V, f = 120 Hz, CADJ = 10 /LF

= 125'C, 1000 hrs

10

3.5

3.0

4.5

3.0

4.5

0.3

1

0.25

1

RMS Output Noise, % of Your 10 Hz,,;; f ,,;; 10 kHz

66

%

1

A
A

0.001

0.001

%

65

65

dB

86

66

86

dB

0.25

1

0.25

KPackage
TPackage

1.2
3

1.5

1.2
3

1.5 'C/W
4 'C/W

KPackage
TPackage

35
50

35
50

'C/W
'C/W

4

1

%

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
Intended to be functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics.

Note 2: These specifications are applicable for power dissipations up to 30W for the TO·3 (K) package and 25W for the TO·220 (T) package. Power dissipation is
guaranteed at these values up to 15V input-output differential. Above 15V differential, power dissipation will be limited by internal protection circuitry. All limits (I.e.,
the numbers in the Min. and Max. columns) are guaranteed to National's AOQL (Average Outgoing Quality Level).
Note 3: Regulation Is measured at a constant junction temperature, using pulse testing with a low duty cycle. Changes in output voltage due to heating effects are
covered under the specifications for thermal regulation.
Note 4: Refer to RETS150K drawing for military specifications of the LMI50K.

1-122

riii:

...

Typical Performance Characteristics

UI

.....
r:s::
Q

Load Regulation

...iii
.

as

I J J••

Adjustment Current
65

~

I~... ~~

10Ul "" I.SA

~ -OA

5.

-0.&

I

VIN=J5V
VOUT= I.V
-25

25

15

125

II

15

21

25

3.

35

-15

1.24

.m

1.23

.....

"r-...

~

0.5 '--'--'--'--'--l-l-.L-.L-.J
-15
-25
25
75
125

\

.s...

3.5

~
...~

.

2.5

1j

1.5

13

"
-25

25

15

-55'';.~ / '

~~

loP

.

~ ~ f'

-25

TEMPERATURE ('CI

Temperature Stability

~ 1.25

Ripple Rejection

1110

I.""
r--

C)DJ"

80

. . r--....
60
jAOJiO

4'

r-

'"..
liI

~

.....

I-

$

2.

;;;

15

20

25

30

CAOJ'O'

V..., ~ lOY
T( = 25"C

10

10.

lk

11k

"'k

OUTPUT CURRENT (A(

Line Transient Response

...

v'" "" 15V

.....
... "
........
...
~~
.......
.. "
~

>1=

0.6

~s:

/

",0

CADJ' "~F

-'.5

CL'O.CADJ"'

l
CL' I !F,

C~DJI" II~

-1

VOUT'" IOV
'gUT'" liOmA

T( - 25'C

r

S;!

10

1110

lk

II.

FREQUENCY (HzI

,.0k

1M

i!!

~ e:
~'"
§!!!
o

Q

:!

~
2.
T(ME,,"I

3.

0

-I

-1.5

0.5
II

0.5

~ ~ -'.5 H.-+-+-t-

~

>z

Load Transient Response

1.5

~E

¥OUT - lOY

•

1M

FREQUENCY (HzI

I.... - 6UO"'"
T(-25'C _

/

'\. ~

V.N -" 15V

2.

Output Impedance

/I

...

lour = DmA

OUTPUT VOLTAGE (VI

---t- CAOJ' 0

CAD}= II""

40

•

35

- "\

,/"

80

II:

I = 120Hz
T(=25'C

10

I.

~

V,N - YOUT = 5V
lOUT "" SOOIllA

II:

;;;

Q

INPUT-'UTPUT DIFFERENTIAL (VI

1.21

~...

Co)

UI

35

Dropout Voltage

8

~
.....
:s::

r-

3.

TEMPERATURE ('CI

'"15

"' ....

~

UI

4'

-1

-15

V

V

45

I;
~ -0.1

liI

Co)

60
55

~ -0.2

~
g

Current Limit

4'

I

1.5

D.:

•

II

2.
TlME(..(

3'

40

TL/H/9061-6

1·123

~

C')

::::!i!

...I

~

C')

::::!i!

...I

~
..-

:!l

r-------------------------------------------------------------------------~

Application Hints
In operation, the LM1S0 develops a nominal 1.2SV reference voltage, VREF, between the output and adjustment terminal. The reference voltage is impressed across program
resistor R 1 and, since the voltage is constant, a constant
current 11 then flows through the output set resistor R2, giving an output voltage of
Your = VREF (1

+

:~)

LOAD REGULATION
The LM1S0 is capable of providing extremely good load regulation but a few precautions are needed to obtain maximum performance. The current set resistor connected between the adjustment terminal and the output terminal (usually 2400) should be tied directly to the output (case) of the
regulator rather than near the load. This eliminates line
drops from appearing effectively in series with the reference
and degrading regulation. For example, a 1SV regulator with
o.oso resistance between the regulator and load will have a
load regulation due to line resistance of O.OSO x lour. If
the set resistor is connected near the load the effective line
resistance will be O.OSO (1 + R2/R1) or in this case, 11.5
times worse.
Figure 2 shows the effect of resistance between the regulator and 2400 set resistor.

+ IADJ R2.

TL1H/9061-7

FIGURE 1
Since the SO ",A current from the adjustment terminal represents an error term, the LM1S0 was designed to minimize
IADJ and make it very constant with line and load changes.
To do this, all quiescent operating current is returned to the
output establishing a minimum load current requirement. If
there is insufficient load on the output, the output will rise.

TL/H/9061-8

FIGURE 2. Regulator with Line Resistance
in Output Lead
With the TO-3 package, it is easy to minimize the resistance
from the case to the set resistor, by using two separate
leads to the case. The ground of R2 can be returned near
the ground of the load to provide remote ground sensing
and improve load regulation.

EXTERNAL CAPACITORS
An input bypass capacitor is recommended. A 0.1 ",F disc
or 1 ",F solid tantalum on the input is suitable input bypassing for almost all applications. The device is more sensitive
to the absence of input bypassing when adjustment or output capacitors are used but the above values will eliminate
the possibility of problems.

PROTECTION DIODES
When external capacitors are used with any IC regulator it is
sometimes necessary to add protection diodes to prevent
the capaCitors from discharging through low current points
into the regulator. Most 10 ",F capacitors have low enough
internal series resistance to deliver 20A spikes when shorted. Although the surge is short, there is enough energy to
damage parts of the IC.

The adjustment terminal can be bypassed to ground on the
LM1S0 to improve ripple rejection. This bypass capacitor
prevents ripple from being amplified as the output voltage is
increased. With a 10 ",F bypass capacitor 86 dB ripple rejection is obtainable at any output level. Increases over
10 ",F do not appreciably improve the ripple rejection at
frequencies above 120 Hz. If the bypass capacitor is used, it
is sometimes necessary to include protection diodes to prevent the capacitor from discharging through internal low current paths and damaging the device.

When an output capacitor is connected to a regulator and
the input is shorted, the output capaCitor will discharge into
the output of the regulator. The discharge current depends
on the value of the capacitor, the output voltage of the regulator, and the rate of decrease of VIN. In the LM150, this
discharge path is through a large junction that is able to
sustain 25A surge with no problem. This is not true of other
types of positive regulators. For output capaCitors of 25 ",F
or less, there is no need to use diodes.
The bypass capacitor on the adjustment terminal can discharge through a low current junction. Discharge occurs
when either the input or output is shorted. Internal to the
LM150 is a 500 resistor which limits the peak discharge
current. No protection is needed for output voltages of 25V
or less and 10 ",F capaCitance. Figure 3 shows an LM150
with protection diodes included for use with outputs greater
than 25V and high values of output capacitance.

In general, the best type of capacitors to use is solid tantalum. Solid tantalum capacitors have low impedance even at
high frequencies. Depending upon capacitor construction, it
takes about 2S ",F in aluminum electrolytic to equal 1 ",F
solid tantalum at high frequencies. Ceramic capacitors are
also good at high frequencies, but some types have a large
decrease in capacitance at frequencies around O.S MHz.
For this reason, 0.01 ",F disc may seem to work better than
a 0.1 ",F disc as a bypass.
Although the LM1S0 is stable with no output capacitors, like
any feedback circuit, certain values of external capacitance
can cause excessive ringing. This occurs with values between soo pF and SOOO pF. A 1 ",F solid tantalum (or 2S ",F
aluminum electrolytic) on the output swamps this effect and
insures stability.
1-124

Application Hints (Continued)
01
lN4UOZ

Dl protects against Cl

M t - - 4 - - - - - VOUT

D2 protects against C2

VOUT

RZ

*) + IADJR2

FT

cz
10 0

= 1.25V ( I +

+

TL/H/90S1-9

FIGURE 3. Regulator with Protection Diodes

Schematic Diagram

TLlH/90S1-10

Typical Applications
Full output current not available
at high input·output voltages.

1.2V-2SV AdJustsble Regulator

tOptlonal-improves transient response. Output capacitors In the range of I
,..F to 1000 ,..F of aluminum or tantalum electrolytic are commonly used to
provide Improved output Impedance and rejection of transients.
'Needed If device Is more than 6 Inches from filter capacitors.

ttvOUT

= 1.25V

(I

+

*) + IADJ (R2)

Note: Usually RI = 240n for LMI50 and RI = 120n for LM350.

TL/H/9061-1

1-125

II

Typical Applications (Continued)
Precision Power Regulator with
Low Temperature Coefficient

....-

Slow Turn-ON 15V Regulator

~~---........"T----'

....." " " " - - - - -.....-VOUT2: 4V

__--~e~T

Uk

lN40DZ

Cl

HI

1000F

375

TUH/9061-14

'Adiusl for 3.75V across AI

TLlH/9061-1S

Adjustable Regulator with Improved
Ripple Rejection

High Stability 10V Regulator
Y,N
15V

01·
1N40D2

*

VOUT
10V
Rl
Zk
5%

Cl

0.1 of

HZ
1.5k
1%

LMIZ9A

R3
Z&7
1%

tSolid tantalum
'Discharges Cl H outpulls shorted 10 ground

TLlH/e061-15
TLIH/9061-16

Digitally Selected Outputs

V,N------t

Regulator and Voltage Reference

I---~~VOUT

RZ
1.4k

TLIH/9061-S

INPUTS
TUH/9061-17

·Sets maximum VOUT

1·126

r-----------------------------------------------------------------------------~

r

i:
.....

Typical Applications (Continued)

U1

o
.....
r

10A Regulator

i:
Co)

0.1

U1

~

r
i:
Co)

2k

0.05
VIN -

0.1

U1

o

0.1

...-'\N~....- - -...--I

I--------....-;....- - t l - - VOUT*

+
22~F

"Minimum load current 50 rnA

TUH/9061-18

oto 30V Regulator

5V Logic Regulator with
Electronic Shutdown'
VIN

35V

H~""""4I~~9UT
~.;;:r:----I

I-+-JVV\t-TTL
lk

II
TL1H/9061-19

"Min output:::::: 1.2V

-lOY
TL/H/9061 -20

Full output current not available at high input-output voltages

1-127

Typical Applications (Continued)
SA Constant Voltage/Constant Current Regulator

R3
0.2
&W
RI
33

OUTPUT
1.2V-30V

3&V
+CI

C3 +

10~Ftl

1'~F

C&
7& pF

tSolid tantalum
-IVTD -IIV
'Lights In constant current mode

R&
330k

R7
220

RI

&k
VOLTAGE
ADJUST
TL/H/90BI-21

12V Battery Charger

V'N2:18V

+

TO 12V
BATTERY

TL/H/90BI-22

1-128

,-----------------------------------------------------------------------------'r
iii:
.....
o
.....
r

Typical Applications (Continued)

CII

Precision Current Limiter

Adjustable Current Regulator

iii:

........."V""~t- lOUT = VREF.
HI

TL/H/9061-24

LM117

w
CII
o

~

r
iii:
w
~

V-5VTO -10V
TL/H/9061-23

1.2V-20V Regulator with
Minimum Program Current

3A Current Regulator

TL/H/9061-26
TUH/9061-25

·Minimum output current::::: 4 rnA

Tracking Preregulator
R2
720

II
VOUT

H3

120

TL/H/9061-27

1·129

Typical Applications (Continued)
Adjusting Multiple On-Card Regulators
with Single Control'

t-......-YOUT

YIN

TL/H/9061-28

tMinimum load-l0 mA
'All outputs within ± 100 mV

AC Voltage Regulator

Simple 12V Battery Charger

120
12Vp-p

24 Vp-p

3A

"v

480~

TL/H/9061-30

'Rs-sets output impedance of charger. ZOUT

~ Rs ( 1 + 1*)

Use of Rs allows low charging rates with fully
charged baHert.
"1000 p.F is recommended to filter out any input transients
TL/H/S061-29

Temperature Controller

Light Controller
LM350

. -...- - - - - -.... YOUT

Rl
1.2k
LAMP
HEATER

TLlH/9061-12

TL/H/S061-11

1·130

Typical Applications

(Continued)

Adjustable 10A Regulator
D.!

..........""",.,.. .--4.&V TO 2&V

5k

&k

TLlH/90S1-31

Current Limited 6V Charger
VIN

9VTD JOV

'Sets peak current (2A for

TL/H/90SI-32

o.aU)

··1000 ,uF is recommended to filter out any input transients.

6A Regulator
AI
0.1

AZ

0.1

-..1\1""-.....---1---1

VIN -

...

CI

+

OUTPUT

I"'

TL/H/9061-2

1-131

II

~National

~ Semiconductor

LM196/LM396 10 Amp Adjustable Voltage Regulator
General Description
The LM196 is a 10 amp regulator, adjustable from 1.25V to
15V, which uses a revolutionary new IC fabrication structure
to combine high power discrete transistor technology with
modern monolithic linear IC processing. This combination
yields a high-performance single-chip regulator capable of
supplying in excess of 10 amps and operating at power levels up to 70 watts. The regulators feature on-Chip trimming
of reference voltage to ±0.8% and simultaneous trimming
of reference temperature drift to 30 ppml"C typical. Thermal
interaction between control circuitry and the pass transistor
which affects the output voltage has been reduced to extremely low levels by strict attention to isothermal layout.
This interaction, called thermal regulation, is 100% tested.
These new regulators have all the protection features of
popular lower power adjustable regulators such as LM117
and LM138, including current limiting and thermal limiting.
The combination of these features makes the LM196 immune to blowout from output overloads or shorts, even if
the adjustment pin is accidentally disconnected. All devices
are "burned-in" in thermal shutdown to guarantee proper
operation of these protective features under actual overload
conditions.
Output voltage is continuously adjustable from 1.25V to
15V. Higher output voltages are possible if the maximum
input-output voltage differential specification is not exceeded. Full load current of 10A is available at all output voltages, subject only to the maximum power limit of 70W and
of course, maximum junction temperature.

The LM196 is exceptionally easy to use. Only two external
resistors are used to to set output voltage. On-chip adjustment of the reference voltage allows a much tighter specification of output voltage, eliminating any need for trimming in
most cases. The regulator will tolerate an extremely wide
range of reactive loads, and does not depend on external
capacitors for frequency stabilization. Heat sink requirements are much less stringent, because overload situations
do not have to be accounted for-only worst-case full load
conditions.
The LM196 is in a TO-3 package with oversized (0.060")
leads to provide best possible load regulation. Operating
junction temperature range is -55'C to + 150·C. The
LM396 is specified for a O'C to + 125'C junction temperature range.

Features
•
•
•
•
•
•
•
•
•

Output pre-trimmed to ± 0.8%
10A guaranteed output current
P + Product Enhancement tested
70W maximum power diSSipation
Adjustable output-1.25V to 15V
Internal current and power limiting
Guaranteed thermal resistance
Output voltage guaranteed under worst-case conditions
Output is short circuit protected

Typical Applications
R1 + R2)
VOUT = (1.25V) ( -R-1-

-.1,

LMI96

+ IADJ (R2)

"R2 should be same type as RI, with TC track·
ing of 30 ppm!'C or beller.

J

tCI is necessary only if main filter capaCitor is
more than 6" away, assuming .. 18 or larger
leads.

V I N I ' - i V I N AD:OUT"'k---------,

I

MAIN
FILTER
CAPACITor

RI*
120

CIt
-_

=~S.07LP.IFD

C3'
+ 25p.F
--'-

-,
TANT

R2**

'For best TC of VOUT, RI should be wirewound
or metal film, I % or beller.

C2tt
......L..4.7p.F
-- rSDLlD

-r-

TANT

-r-

LOAD

-r-

ttC21s not absolulely necassary, but is suggested to lower high frequency outpul impedance.
Outpul capacitors in the range 01 1 fLF to
1000 fLF of aluminum or tantalum electrolytic
are commonly used to provide Improved output Impedance and reiection of transienta.

'e3

I

improves ripple rejection, output imped·

ance, and noise. C2 should be 1 fLF or larger
close to the regulator H C3 is used.

TL/H/9059-1

FIGURE 1. BasiC 1.25V to 15V Regulator

1-132

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Power Dissipation

Storage Temperature

- 65'C to

Lead Temperature (Soldering, 10 seconds)

+ 150'C
300'C

EsD rating to be determined

Internally Limited

Input-Output Voltage Differential

20V

Operating Junction Temperature Range

+ 150'C
+ 200'C
O'C to + 125'C
O'C to + 175'C

LM196 Control Section
Power Transistor

- 55'C to
- 55'C to

LM396 Control Section
Power Transistor

Electrical Characteristics (Note 1)
Parameter

LM196

Conditions

LM396

Units

Min

Typ

Max

Min

Typ

Max

Relerence Voltage

lOUT = 10 mA

1.24

1.25

1.26

1.23

1.25

1.27

V

Relerence Voltage
(Note 2)

VMIN ~ (VIN - VOUT) ~ 20V
10 mA ~ lOUT 10A, P ~ PMAX
Full Temperature Range

1.22

1.25

1.28

1.21

1.25

1.29

V

Line Regulation
(Note 3)

VMIN ~ (VIN - VOUT) ~ 20V
Full Temperature Range

0.005

0.01
0.05

0.005

0.02
0.05

"ioN
%N

Load Regulation
LM196/LM396
(Note 4)

10 mA ~ lOUT ~ 10A
VMIN ~ VIN - VOUT ~ 10V, P ~ PMAX
Full Temperature Range

0.1

%/A

0.15

"lolA

Ripple Rejection
(Note 5)

CADJ = 25 /-IoF, 1= 120 Hz
Full Temperature Range

Thermal Regulation
(Note 6)

VIN - VOUT = 5V, lOUT = 10A

0.003

Average Output Voltage
Temperature Coefficient

TjMIN ~ Tj ~ TjMAX
(See Curves lor Limits)

0.003

0.1
0.15
60
54

74

66
54
0.005

74
0.003

dB
dB
0.Q15

%/W
%rC

0.003
100

/-loA

Adjustment Pin Current
Change (Note 7)

10 mA ~ lOUT ~ 10A
3V ~ VIN - VOUT ~ 20V
P ~ PMAX, Full Temperature Range

3

3

/-loA

Minimum Load Current
(Note 9)

2.5V ~ (VIN - VOUT) ~ 20V
Full Temperature Range

10

10

mA

Current Limit
(Note 8)

2.5 ~ (VIN - VOUT ~ 7V
VIN - VOUT = 20V

20
8

A
A

Adjustment Pin Current

50

10
1.5

14
3

100

20
8

50

10
1.5

14
3

Rms Output Noise

10 Hz ~ I ~ 10 kHz

Long Term Stability

Tj = 125'C, t = 1000 Hours

0.3

1.0

0.3

1.0

%

Thermal Resistance
Junction to Case
(Note 10)

Control Circuitry
Power Transistor

0.3
1.0

0.5
1.2

0.3
1.0

0.5
1.2

'C/W
'C/W

0.001

1-133

0.001

%VOUT

CD
CD
C")

:::i

Electrical Characteristics (Note 1) (Continued)

...I

.....
CD

Parameter

....

:::i
...I

Power Dissipation (PMAXl
(Note 11)

7.0V:S: VIN - VOUT:S: 12V
VIN - VOUT = ISV
VIN - VOUT = 18V

Min

Typ

70
SO
36

100

Drop-Out Voltage
LM196/LM396
Note

LM396

LM196

Conditions

CD

lOUT = lOA,
Full Temperature Range
1: Unless otherwise stated, these specifications apply for TI ~ 25'C, VIN

2.1

Max

Min

Typ

70
SO
36

100

2.S
2.7S

2.1

Units
Max
W
W
W
2.S
2.7S

V

- Your ~ 5V, lOUT ~ 10 mA to lOA.

Note 2: This is a worst-case specification which includes all effects due to input voltage, output current, temperature, and power dissipation. Maximum power
(PM'xl is specified under Electrical Characteristics.
Note 3: Line regulation is measured on a short~pulse. low-duty-cycle basis to maintain constant junction temperature. Changes in output voltage due to thermal
gradients or temperature changes must be taken into account separately. See discussion of Line Regulation under Application Hints.
Note 4: Load regulation on the 2·pin package is determined primarily by the voltage drop along the output pin. SpecHications apply for an external Kelvin sense
connnection at a point on the output pinY.' from the bollom of the package. Testing Is done on a short·pulse-width, low·duly·cycle basis to maintain constant
junction temperature. Changes in output voltage due to thermal gradients or temperature changes must be taken into account separately. See discussion of Load
Regulation under Application Hints.
Note 5: Ripple rejection is measured with the adjustment pin bypassed with 25 f'F capacitor, and Is therefore independent of output voltage. With no load or
bypass capacitor, ripple rejection is determined by line regulation and may be calculated from; RR ~ 20 log10 [100/(K X Vour)] where K Is line regulation
expressed in %/V. At frequencies below 100 Hz, ripple reiection may be limited by thermal effects, if load current is above IA.
Note 6: Thermal regulation is defined as the change in output voltage during the time period of 0.2 ms 10 20 ms after a change in power dissipation in the regulator,
due to either a change in input voltage or output current. See graphs and discussion of thermal effects under Application Hints.

Note 7: Adjustment pin current change is specHied for the worst-case combination of input voltage, output current, and power dissipation. Changes due to
temperature must be taken into account separately. See graph of adjustment pin current vs temperature.
Note 8: Current limit is measured 10 ms after a short is applied to the output. DC measurements may differ slightly due to the rapidly changing junction temperature,
tending to drop slightly as temperature increases. A minimum available load current of 10A is guaranteed over the full temperature range as long as power
dissipation does not exceed 70W, and VIN - VOUT is less than 7.0V.
Note 9: Minimum load current of 10 mA is normally satisfied by the resistor divider which sets up output voltage.

Note 10: Total thermal reSistance, junction-to-ambient, will include junction-to-caSB thermal resistance plus interface resistance and heat sink resistance. Sse
discussion of Heat Sinking under Application Hints.
Note 11: Although power dissipation is internally limited, electrical specifications apply only for power dissipation up to the limits shown. Deraling with temperature
is a function of both power transistor temperature and control area temperature, which are specified differently. See discussion of Heat Sinking under Application
Hints. For VIN - VOUT less than 7V, power dissipation is limited by current limit of 10A.
Note 12: Dropout voltage is input-output voltage differential measured at a forced reference voltage of I.ISV. with a lOA load. and is a measurement of the
minimum Input/output differential at full load.

Application Hints

is guaranteed to dissipate up to 70W continuously, as long
as the maximum junction temperature limit is not exceeded.
This requires careful attention to all sources of thermal resistance from junction-to-ambient, including junction-tocase resistance, case-to-heat sink interface resistance
(0.1-1.0·C/W), and heat sink resistance itself. A good thermal joint compound such as Wakefield type 120 or Thermalloy Thermocote must be used when mounting the LM196,
especially if an electrical insulator is used to isolate the regulator from the heat sink. Interface resistance without this
compound will be no better than O.S·C/W, and probably
much worse. With the compound, and no insulator, interface
resistance will be 0.2·C/W or less, assuming O.OOS" or less
combined flatness run-out of TO-3 and heat sink. Proper
torquing of the mounting bolts is important to achieve minimum thermal resistance. Four to six inch pounds is recommended. Keep in mind that good electrical, as well as thermal, contact must be made to the case.

Further improvements in efficiency can be obtained by using
Schottky diodes or high efficiency diodes with lower forward
voltage, combined with larger filter capacitors to reduce ripple. However, this reduces the voltage difference between
input and drive pins and may not allow sufficient voltage to
fully saturate the pass transistor. Special transformers are
available from Signal Transformer that have a 1V tap on the
output winding to provide the extra voltage for the drive pin.
The transformers are available as standard items for SV applications at SA, lOA and 20A. Other voltages are available
on special request.
Heat Sinking
Because of its extremely high power dissipation capability,
the major limitation in the load driving capability of the
LM196 is heat sinking. Previous regulators such as LM109,
LM340, LM117, etc., had internal power limiting circuitry
which limited power dissipation to about 30W. The LM196

1-134

Application Hints (Continued)
The actual heat sink chosen for the LM196 will be determined by the worst-case continuous full load current, input
voltage and maximum ambient temperature. Overload or
short circuit output conditions do not normally have to be
considered when selecting a heat sink because the thermal
shutdown built into the LM196 will protect it under these
conditions. An exception to this is in situations where the
regulator must recover very quickly from overload. The
LM196 may take some time to recover to within specified
output tolerance following an extended overload, if the regulator is cooling from thermal shutdown temperature (approximately 175·) to specified operating temperature (125·C or
150·C). The procedure for heat sink selection is as follows:

quent cost savings in the transformer and heat sink. Sometimes several capacitors in parallel are better to decrease
series resistance and increase heat disSipating area.
After the raw supply characteristics have been determined,
and worst-case power dissipation in the LM196 is known,
the heat sink thermal resistance can be found from the
graphs titled Maximum Heat Sink Thermal Resistance.
These curves indicate the minimim size heat sink required
as a function of ambient temperature. They are derived from
a case-to-control area thermal resistance of 0.5·C/W and a
case-to-power transistor thermal resistance of 1.2"C/W.
0.2·C/W is assumed for interlace resistance. A maximum
control area temperature of 150·C is used for the LM196
and 125·C for the LM396. Maximum power transistor temperature is 200·C for the LM196 and 175·C for the LM396.
For conservative designs, it is suggested that when using
these curves, you assume an ambient temperature 25·C50·C higher than is actually anticipated, to avoid running the
regulator right at its design limits of operating temperature.

Calculate worst-case continuous average power dissipation in the regulator from P = (VIN - VOUT) x (lOUT)' To
do this, you must know the raw power supply voltage/ current characteristics fairly accurately. For example, consider a 10V output with 15V nominal input voltage. At full
load of lOA, the regulator will dissipate P = (15 - 10) X
(10) = 50W. If input voltage rises by 10%, power dissipation will increase to (16.5 - 10) x (10) = 65W, a 30%
increase. It is strongly suggested that a raw supply be
assembled and tested to determine its average DC output
voltage under full load with maximum line voltage. Do not
over-design by using unloaded voltage as a worst-case,
since the regulator will not be dissipating any power under
no load conditions. Worst-case regulator dissipation normally occurs under full load conditions except when the
effective DC resistance of the raw supply (60 V / 601) is larger than (VIN" - Vour)/21IL, where VIN' is the lightly-loaded raw supply voltage and IlL is full load current. For (VIN"
- Your) = 5V - av, and IlL = 5A-l0A, this gives a
resistance of 0.25n to o.an. If raw supply resistance is
higher than this, the regulator power dissipation may be
less at full load current, then at some intermediate current, due to the large drop in input voltage. Fortunately,
most well designed raw supplies have low enough output
resistance that regulator dissipation does maximize at full
load current, or very close to it, so tedious testing is not
usually required to find worst-case power dissipation.
A very important consideration is the size of the filter capacitor in the raw supply. At these high current levels, capacitor
size is usually dictated by ripple current ratings rather than
just obtaining a certain ripple voltage. Capacitor ripple current (rms) is 2-3 times the DC output current of the filter. If
the capacitor has just 0.05n DC resistance, this can cause
30W internal power dissipation at lOA output current. Capacitor life is very sensitive to operating temperature, decreasing by a factor of two for each 15·C rise in internal
temperature. Since capacitor life is not all that great to start
with, it is obvious that a small capacitor with a large internal
temperature rise is inviting very short mean-time-to-failure.
A second consideration is the loss of usable input voltage to
the regulator. If the capacitor is small, the large dips in the
input voltage may cause the LM196 to drop out of regulation .. 2000 ",F per ampere of load current is the minimum
recommended value, yielding about 2 Vp-p ripple of 120 Hz.
Larger values will have longer life and the reduced ripple will
allow lower DC input voltage to the regulator, with subse-

A quick look at the curves show that heat sink resistance
(8SA) will normally fall into the range of 0.2·C/W-l.5·C/W.
These are not small heat sinks. A model 441, for instance,
which is sold by several manufacturers, has a 8SA of
0.6·C/W with natural convection and is about five inches on
a side. Smaller sinks are more volumetrically efficient, and
larger sinks, less so. A rough formula for estimating the volume of heat sink required is: V = 50/8SA1.5 CU. IN. This
holds for natural convection only. If the heat sink is inside a
small sealed enclosure, 8SA will increase substantially because the air is not free to form natural convection currents.
Fan-forced convection can reduce 8SA by a factor of two at
200 FPM air velocity, and by four at 1000 FPM.
Ripple Rejection
Ripple rejection at the normal ripple frequency of 120 Hz is
a function of both electrical and thermal effects in the
LM196. If the adjustment pin is not bypassed with a capacitor, it is also dependent on output voltage. A 25 ",F capacitor from the adjustment pin to ground will make ripple rejection independent of output voltage for frequencies above
100 Hz. If lower ripple frequencies are encountered, the capacitor should be increased proportionally.
To keep in mind that the bypass capacitor on the adjustment pin will limit the turn-on time of the regulator. A 25 ",F
capacitor, combined with the output divider resistance, will
give an extended output voltage settling time following the
application of input power.
Load Regulation (LM196/LM396)
Because the LM196 is a three-terminal device, it is not possible to provide true remote load sensing. Load regulation
will be limited by the resistance of the output pin and the
wire connecting the regulator to the load. For the data sheet
specification, regulation is measured 1/4" from the bottom
of the package on the output pin. Negative side sensing is a
true Kelvin connection, with the bottom of the output divider
returned to the negative side of the load.

1-135

II

~ r-------------------------------------------------------------------~

m

C')

:=l

i....
:=l

Application Hints (Continued)
Although it may not be immediately obvious, best load regulation is obtained when the top of the divider is connected
directly to the output pin, not to the load. This is illustrated in
Figure 2. If R1 were connected to the load, the effective
resistance between the regulator and the load would be
(Rw)

TC = Temperature coefficient of output voltage.
9jA = Thermal resistance from junction to ambient. 9jA is

approximately 0.5°C/W + 9 of heat sink.
For the same conditions as before, with TC = 0.003%/OC,
and 9jA = 1.5°C/W, the change in output voltage will be
0.1S%. Because these two thermal terms can have either
polarity, they may subtract from, or add to, electrical load
regulation. For worst-case analysis, they must be assumed
to add. If the output of the regulator is trimmed under load,
only that portion of the load that changes need be used in
the previous calculations, significantly improving output accuracy.

x (R2 ~ R1)

Rw = Line Resistance
Connected as shown, Rw is not multiplied by the divider
ratio. Rw is about 0.0040. per foot using 16 gauge wire. This
translates to 40 mV1ft at 10A load current, so it is important
to keep the positive lead between regulator and load as
short as possible.

Line Regulation
Electrical line regulation is very good on the LM196-typically less than 0.005% change in output voltage for a 1V
change in input. This level of regulation is achieved only for
very low load currents, however, because of thermal effects. Even with a thermal regulation of 0.002%.W, and a
temperature coefficient of 0.003%I"C, DC line regulation
will be dominated by thermal effects as shown by the following example:

Rw

PARASITIC
LM396
LINE R:S~S}ANCE
VIN
VOUTflf
''''
ADJ
~ '\

J

DD NOT CONNECT
RI TO LOAD

RI

I

+
LOAD

I

Assume VOUT = 5V, VIN = 9V, lOUT = SA
Following a 10% change in input voltage (0.9), the output
will change quickly (~1 00 /-Ls), due to electrical effects, by
(0.005%V) X (0.9V) = 0.0045%. In the next 20 ms, the
output will change an additional (0.002%/W) X (SA) X
(0.9V) = 0.0144% due to thermal gradients across the die.
After a much longer time, determined by the time constant
of the heat sink, the output will change an additional
(0.003%I"C) X (BA) X (0.9V) X (2°C/W) = 0.043% due to
the temperature coefficient of output voltage and the thermal resistance from die to ambient. (2°C/W was chosen for
this calculation). The sign of these last two terms varies
from part to part, so no assumptions can be made about any
cancelling effects. All three terms must be added for a proper analysis. This yields 0.0045 + 0.D144 + 0.043 =
0.062% using typical values for thermal regulation and temperature coefficient. For worst-case analysis, the maximum
data sheet specifications for thermal regulation and temperature coefficient should be used, along with the actual thermal resistance of the heat sink being used.

R2

~~

----------------~Ip_----~
CONNECT R2
TO LOAD
TL/H/9059-2

FIGURE 2. Proper Divider Connection
The input resistance of the sense pin is typically 6 ko., modeled as a resistor between the sense pin and the output pin.
Load regulation will start to degrade if a resistance higher
than 100. is inserted in series with the sense. This assumes
a worst-case condition of 0.5V between output and sense
pins. Lower differential voltage will allow higher sense series
resistance.
Thermal Load Regulation
Thermal, as well as electrical, load regulation must be considered with IC regulators. Electrical load regulation occurs
in microseconds, thermal regulation due to die thermal gradients occurs in the 0.2 ms-20 ms time frame, and regulation due to overall temperature changes in the die occurs
over a 20 ms to 20 minute period, depending on the time
constant of the heat sink used. Gradient induced load regulation is calculated from

Paralleling Regulators
Direct paralleling of regulators is not normally recommended because they do not share currents equally. The regulator with the highest reference voltage will supply all the current to the load until It current limits. With an 1BA load, for
instance, one regulator might be operating in current limit at
16A while the second device is only carrying 2A. Power dissipation In the high current regulator is extremely high with
attendant high junction temperatures. Long term reliability
cannot be guaranteed under these conditions.
Quasi-paralleling may be accomplished if load regulation is
not critical. The connection shown in Figure 5a will typically
share to within 1A, with a worst-case of about 3A. Load
regulation is degraded by 150 mV at 20A loads. An external
op amp may be used as in Figure 5b to improve load regulation and provide remote sensing.

AVOUT = (VIN - VOUT) X (AIOUT) X (/3)

/3

= Thermal regulation specified on data sheet.

For VIN = 9V, VOUT = 5V, AIOUT = 10A, and /3 =
0.005%/W, this yields a 0.2% change in output voltage.
Changes in output voltage due to overall temperature rise
are calculated from
VOUT = (VIN- VOUT) X (AIOUT) X (TC) X (9jA)

1-136

r-----------------------------------------------------------------------------'r

:s::
....
CD

Application Hints (Continued)
VNOM = Nominal line voltage AC rms
VLQW = Low line voltage AC rms

Input and Output Capacitors
The LM196 will tolerate a wide range of input and output
capacitance, but long wire runs or small values of output
capacitance can sometimes cause problems. If an output
capacitor is used, it should be 1 jLF or larger. We suggest 10
jLF solid tantalum if significant improvements in high frequency output impedance are needed (see output impedance graph). This capacitor should be as close to the regulator as possible, with short leads, to reduce the effects of
lead inductance. No input capacitor is needed if the regulator is within 6 inches of the power supply filter capacitor,
using 18 gauge stranded wire. For longer wire runs, the
LM196 input should be bypassed locally with a 4.7 jLF (or
larger) solid tantalum capacitor, or a 100 jLF (or larger) aluminum electrolytic capacitor.

lOUT = DC output current

VRIPPLE = 2 Vp-p, VNOM = 115V,
VLQW = 105V

. C
(5.3 X 10- 3) (lOUT)
Capacltor
=
V
2 X RIPPLE
(5.3 X 10- 3)(10)
F
=
2
= 26,500 jL

Correcting for Output Wire Losses (LM196/LM396)

The diodes used in a full-wave rectified capacitor input supply must have a DC current rating considerably higher than
the average current flowing through them. In a 10A supply,
for instance, the average current through each diode is only
5A, but the diodes should have a rating of 1OA-15A. There
are many reasons for this, both thermal and electrical. The
diodes conduct current in pulses about 3.5 ms wide with a
peak value of 5-8 times the average value, and an rms
value 1.5-2.0 times the average value. This results in long
term diode heating roughly equivalent to 10A DC current.
The most demanding condition however, may be the one
cycle surge through the diode during power turn on. The
peak value of the surge is about 10-20 times the DC output
current of the supply, or 1OOA-200A for a 10A supply. The
diodes must have a one cycle non-repetitive surge rating of
200A or more, and this is usually not found in a diode with
less than 10A average current rating. Keep in mind that
even though the LM196 may be used at current levels below 10A, the diodes may still have to survive shorted output
conditions where average current could rise to 12A-15A.
Smaller transformers and filter capacitors used in lower current supplies will reduce surge currents, but unless specific
information is available on worst-case surges, it is best not
to economize on diodes. Stud-mounted devices in a DO-4
package are recommended. Cathode-to-case types may be
bolted directly to the same heat sink as the LM196 because
the case of the regulator is its power input. Part numbers to
consider are the 1N1200 series rated at 12A average current in a DO-4 stud package. Additional types include common cathode duals in a TO-3 package, both standard and
Schottky, and various duals in plastic filled assemblies.
Schottky diodes will improve efficiency, especially in low
voltage applications. In a 5V supply for instance, Schottky
diodes will decrease wasted power by up to 6W, or alternatively provide an additional 5% "drop out" margin for lowline conditions. Several manufacturers are producing "high
efficiency" diodes with a forward voltage drop nearly as
good as Schottkys at high current levels. These devices do
not have the low breakdown voltages of Schottkys, so are
much less prone to reverse breakdown induced failures.

Transformers and Diodes
Proper transformer ratings are very important in a high current supply because of the conflicting requirements of efficiency and tolerance to low-line conditions. A transformer
with a high secondary voltage will waste power and cause
unnecessary heating in the regulator. Too Iowa secondary
voltage will cause loss of regulation under low-line conditions. The following formulas may be used to calculate the
required secondary voltage and current ratings using a fullwave center tap:

+ VREG + VRECT + VRIPPLE)

.J2

(~:~:) (1.1)')
Irms = (lOUT) (1.2)
where:

105 1.1

= 8.01 Vrms

Three-terminal regulators can only provide partial Kelvin
load sensing (see Load Regulation). Full remote sensing
can be added by using an external op amp to cancel the
effect of voltage drops in the unsensed positive output lead.
In Figure 7, the LM301A op amp forces the voltage loss
across the unsensed output lead to appear across R3. The
current through R3 then flows out the V- pin of the op amp
through R4. The voltage drop across R4 will raise the output
voltage by an amount equal to the line loss, just cancelling
the line loss itself. A small ('" 40 mY) initial output voltage
error is created by the quiescent current of the op amp.
Cancellation range is limited by the maximum output current
of the op amp, about 300 mV as shown. This can be raised
by increasing R3 or R4 at the expense of more initial output
error.

V
- (VOUT
rms -

+ 2.2 + 1.2 + 1) (~)
,f2

(Full-wave center tap)

VOUT = DC regulated output voltage
VREG = Minimum input-output voltage of regulator
VRECT = Rectifier forward voltage drop at three times DC
output current
VRIPPLE = 1/2 peak-to-peak capacitor ripple voltage
(5.3 X 10- 3) (lOUT)
2C
'The factor of 1.t is only an approximate factor accounting for load regula·
tion of the transformer.

1-137

Q)

~

Example: lOUT = 10A, VOUT = 5V
Assume: VREG = 2.2V, VRECT = 1.2V

= (5
V
rms

.....
r
:s::
CD

Q)

U)

en
C')

~

r------------------------------------------------------------------------------------------,
Typical Performance Characteristics

i....

~

Minimum Input·Output
Differential'

Reference Drift

~

~~

2.0

t-+-:7:=~:::':-:::::±:-1-

~
~
;:::

z

1.0

~
is

l!I
ill

~

!

-1.0 ~~'-t-t±C':'YIIi

..

-2.0

t-+-+-t-+-+-i-'

-&0

&0

I.B

~

1.2

...... ~ ~~
i'"""

TI·!",5..

I.B
1.4

1..;""

1.0

1&0

100

~

2.0

co

,.:.

"'CD
~

.
5;
I!:

2.2

o

~

~ ~I:;::I'

~~~

"~ ~
~TI'

I'

2

TEMPERATURE I"CI

Minimum Input-output
Differential'

3 4

Ti 'I&O"C

~

~
is

....
I-

OOT- I-t-

& I

.

~
c

7

8

I!:

~
II!

--

2.3
2.2
2.1
2.0
I.D
I.B

........

1.&
lA
1.3

J

I

['I...,

"

1.1

IOUT'10A

...... ~JI

l"'--,

1.7

~IOUT'&A

N

lOUT' 2A .......

-&0 -2&

D 10

-

.....

J I
I I

OUTPUT CURRENT {AI

0

2&

&0

7& 100 12& 1&0

JUNCTION TEMPERATURE rCI
TLfHf9059-3

'V,N Is reduced until oulput drops 2%

Maximum Power
Dissipation"

Current Limit
20

5
z

14
12

U

10
8

I-

.
..."
::l

I-

-'"

18
II

Tj~25"C-t-

.

MEASURED 100 m.
AFTER SHDRT IS
"APPLIED

""

I

I!:

~
~
2

./GUARAlfrEfIJ ' " I\..
MINIMUM

o I

I

~

I

o

'V,N Is reduced until output drops 2%

10

15

20

25

120
110
100
90
10
70
60
50
40
3D
20
10
0

Maximum Heat Sink
Thermal Resistance"
1.5

LM1D6
LM396

...~"'
u

z

1.3

...

1.1
0.9

i...
.~ $
-~~i~~
~<'
...
0.7

c

0.5
0.3

~

0.1

o

3D
60
DO
120
CASE TEMPERATURE I"CI

0

INPUT·OUTPUT DIFFERENTIAL {VI

LM396

~

.. <'

<''\I

...'

o

H

I\.

&D

~

&D

~O

120

POWER DISSIPATlDN (WI
TLfHf9059-4

•As limited by maximum Junction temperature.

TO·3 Interface Thermal
Resistance Using Thermal
Joint Compound

Maximum Heat Sink
Thermal Resistance·
1.5

...~
"'uz
c

.
....
...
!1i

::l
c

~

TA' 20"C
TA = 100"C
TA' 80"C
TA'IO"C

1.3
1.1
0.9

NA~~"C

0.7

i
..

!

LM196

40

10

80

100

POWER DISSIPATION {WI

./

NO INSULATOR

0.1&

,r

t--

/'

/

I-~T'

iJ

/'

0.1

/

~ O.DB

!!

0.1 TA =12O"C
20

..

Thermal Regulation

./

I

O.z

l!I

"'
~

0.&
0.3

~

I

'See "Heat Sinking" under Applications Hints.

Ti" Z&"c

I
J

~

MOUNTING THICKNESS' 0.18" ALUM•

JOINT COMPOUND' 0.0018

re·.

~~L

~1i~&W
o

120
TDTAL SURFACE RUNDUT {MILS/INCHI
{INCLUDES TDol AND HEAT SINK RUNDUn

I

2 4 8 8 W 12 " 1& 1& H
TIMElm.1
TLfHf9059-5

'See "Heat Sinking" under Application Hints.

1·138

Typical Performance Characteristics

(Continued)

Ripple Rejection

Reference Voltage Noise'
80

10-4

~-IOUT' lA_

r 1~~iJ \IJI~

Oil

..ti
...;J
it

::!!

z

0:

60

oIoIIIlIoo.

70
60

~
--'
-

111111

11111
11111

50
40

VIN-V.,qUT'· 6V

3D

BYPASSED C· 26 pF
CDUT"I~::,~-1oopF

~~~~~T~ENT PIN

;

70
65
80
65
50
4&

20
100

lk

0.1

lOOk

10k

75

I

10

100

012346878910

FREQUENCY 1kHz)

FREQUENCY 1Hz)

OUTPUT CURRENT IA)
TL/H/9059-6

'To obtain output noisa, multiply by
VOUT/1,25 if adiustmant pinls not bypassad.

Output Impedance
Adjustment Pin Bypassed
(C = 25 ",F)

Adjustment Current

10

65
60

~

55

,/

50

V,N'1oV,CADJ=0

i-""

.

§

",

lil

/

45

Output Impedance'
10

:li

0.1

~

40

0.01

0.01

35
3D

0.001

0.001
-75

-25

25

125

75

10

100

TEMPERATURE ec)

lk

10k

lOOk

1M

10

100

1k

10k

lOOk

1M

FREQUENCY 1Hz)

FREQUENCY 1Hz)

TL/H/9059-7

'For output voltagas othar than 5V, multiply vartical scala raadings by VOUT/5.

Line Transient Response
Adjustment Pin Bypassed
AV,N= 0.5V

~1
~

~ 50mV

IT
~

1r,f""1ps

Load Transient Response
Adjustment Pin Bypassed
AloUT" lA
'DC' lA - IDA

-+COUT'O

Line Transient Response'

t r.,S:1DDns

I-~VIN

1r".1 PI

=O.&V

f-COUT'O

f-.CO UT • O

~rIPFTANT
CADI' 25 pF ALL TRACES_

Il COUT =1 pFTANT

II

CqUT'1 pF TANI
CADI,25pF
COUT=10PFTrN~ ALL TRACES

IOU~"'1A~1JA

'r"r
40

60
80
TlME(p.)

'OUT'"1A

VOUT'5V
'- COUT" 100 pF ALU~-t++-

rCOUT = 100 pF ALUM
100

120

IDA

COUT' 10 pFTANT

10 pF TANT

I I I

C U ·.100pF ALUM
20

r-~OUT"

20

40

60
TIME Ip.)

60

100

120

20

40

&0

10

100

120

TIME (p.)
TUH/9059-8

'With no adiustmant pin bypass. For output voltagas 01her than 5V, multiply vartlcal scala by
VOUT/5.

1-139

CD

G)

~

Typical Performance Characteristics

...J

~

(Continued)

Load Transient Response"

z

G)

~

~l

-

Q

~

D.ZV

;T

_",$:100 RI

1l10UT" tA
10C ·tA- tOA

"{-

COUTo 0

V-

COUT' I #FTANT _
VOUT'5V

!.oI!

COUT' 10 #FTANT

.:r

+- r--

~f--COUT= 1oo#F ALUM- r-r-

20

40

60
60
nMEI#sl

100

120
TL/H/9059-9

'With no adjustment pin bypass. For output voltages other than 5V, multiply vertical scale by
VOllT /5 .

Typical Applications (Continued)

..---....

k:~---------

VOUT" 3.75V + (11 mA x R21
• 5.0 VOC

Uk
5%

383
1%

OUTP1~~
;Z...--~..
ADJUST

LM336
2.5V

Cl
1o#f
TANT

+

R2
117

1%

TL/H/9059-10

"'Regulation can be improved by adding an LM336 reference diode to increase the effective reference
voltage to 3.75V. Load and line regulation are improved by 3:1, including thermal effects.

FIGURE 3. Improving Regulation·
R3'

"'RS is selected to supply partial load current. Therefore, a minimum load
must always be maintained to prevent the regulated output from rising uncontrolled. R3 must be greater than (VMAX - VOUT)flMIN, where VMAX is
worsl-case high input voltage, and IMIN is the minimum load current. R3
must be rated for at least (VIN - VOUT)2/R3 watts. Regulator power dissipation will be reduced by a factor of 2-3 in a typical situation where minimum
load current is 1/2 full load current. Regulator dissipation will peak at:
VIN

= (R3)(IOUT) + VOUT
2

and will be equal to:
PMAX

=

(R3)(IOUT)2
--4--Assumlng: (R3)(IOUT) :s;; VMAX - VOUT

A few words of caution; (I) R3 power rating must be increased to (VMAX)21
R3 if continuous output shorts are possible. (2) Under normal load conditions, system power dissipation is not changed, but under short circuR conditions system power dissipation Increases by (VIN)2/R3 watts over the al-

ready high power of a shorted regulator. The LMI96 will not be harmed and
neither will R3 if it is rated properly, but the raw supply components must be
able to withstand the overload also. Thermal shutdown of the LMI96 will
probably occur for sustained shorts, somewhat alleviating the problem.
TL/H/9059-11

FIGURE 4. Reducing Regulator Power Dissipation

1·140

Typical Applications (Continued)

rLM3ii-l

0.015.

"--lV'N ADJVour I~------~-------II
I
I

--T--...I

I

I r---~

I:

0.015·

I

R3

sa

+

TLlH/9059-12

FIGURE 5a. Paralleling Regulators

TL/H/S05S-13

'2 feet of #18 CU wire
"Total voltage drop across output wire and connector should not exceed O.3V

FIGURE 5b

R2
R3
OUTPUT
TRIM

TL/H/905S-14
Output will be within ±20 mV at 25'C, no load. Regulation of tracking units Is Improved by Vour/l.25 compared to a normal connection.
Regulation of master unit Is unchanged. Load or Input voltage changes on slave units do not affect other units, but all units will be affected
by changes on master. A short on any output will cause all other outputs to drop to approximately 2V.

FIGURE 6. Tracking Regulators

1-141

Typical Applications (Continued)

R3

25

-VIN-4_----------{~------;.....-..:...~TL/H/9059-15

·Parasatic line resistance created by wiring
connector., or parallel ballasting.

FIGURE 7. Correcting for Line Losses

STANDARD NPN

POWER NPN

/
TL/H/9059-16

Power NPNs have low collecter resistance, and do not require collector bond wires. Collectors are all common to substrate.
Siandard NPNs are still isolated.

FIGURE 8. Process Technology

Connection Diagram
Metal Can Package

CASE IS

VIN

TL/H/9059-18

Bottom View
Order Number LM196K STEEL or LM396K STEEL
See NS Package Number K02B

1·142

en

n

:::r
(I)

3

a
DRIVE" (;'

VIN

C

~.
Rl
310

R2
310

RJ
120

....D)

R4
50

3

*

R6
200k

!I

(D2~

T Wol

'

~4k

II

1
~RB

01
6.3V

~

......

-c I r·
n~

r'~

~
to)

"'.u~

_.~

L.

~

I

~I
_.:

~

.~

I

T

L;-.~6

u

~400
/

I

02
6.JV

~R22
160

03
6.3V

-- . .J

RI2
12
R2B
0.01

••

....,.,"

0·"1
AOJ

'I

,

5

,~

R25
3
VOUT

SENSE"
TUH/9059-17

'Drive is tied to VIN and sense is tied to VOUT on LMI 96 and LM396.

96£11111/96U111

II

r-------------------------------------------------------------------------,
:!! ~National
~

.....
..CO)
~

~ Semiconductor

LM317L 3-Terminal Adjustable Regulator
General Description
The LM317L is an adjustable 3-terminal positive voltage
regulator capable of supplying 100 rnA over a 1.2V to 37V
output range. It is exceptionally easy to use and requires
only two external resistors to set the output voltage. Further,
both line and load regulation are better than standard fixed
regulators. Also, the LM317L is available packaged in a
standard TO-92 transistor package which is easy to use.
In addition to higher performance than fixed regulators, the
LM317L offers full overload protection. Included on the chip
are current limit, thermal overload protection and safe area
protection. All overload protection circuitry remains fully
functional even if the adjustment terminal is disconnected.

Features
•
•
•
•
•
•
•

Adjustable output down to 1.2V
Guaranteed 100 rnA output current
Line regulation typically 0.Q1 % V
Load regulation typically 0.1 %
Current limit constant with temperature
Eliminates the need to stock many voltages
Standard 3-lead transistor package
• BO dB ripple rejection
• Output is short circuit protected
Normally, no capacitors are needed unless the device is
situated more than 6 inches from the input filter capacitors
in which case an input bypass is needed. An optional output
capacitor can be added to improve transient response. The
adjustment terminal can be bypassed to achieve very high
ripple rejection ratios which are difficult to achieve with standard 3-terminal regulators.

Besides replacing fixed regulators, the LM317L is useful in a
wide variety of other applications. Since the regulator is
"floating" and sees only the input-to-output differential voltage, supplies of several hundred volts can be regulated as
long as the maximum input-to-output differential is not exceeded.
Also, it makes an especially simple adjustable switching regulator, a programmable output regulator, or by connecting a
fixed resistor between the adjustment and output, the
LM317L can be used as a precision current regulator. Supplies with electronic shutdown can be achieved by clamping
the adjustment terminal to ground which programs the output to 1.2V where most loads draw little current.
The LM317L is available in a standard TO-92 transistor
package and the SO-8 package. The LM317L is rated for
operation over a - 25'C to 125'C range.

Connection Diagram
V I N O S NC
VOUT
2
7 VOUT

Your

3

ADJ4
BOTTOM VIEW

Vour

TL/H/B064-5

TL/H/B0B4-4

Order Number LM317LZ
See NS Package
NumberZ03A

6

SHC

Order Number LM317LM
See NS Package
Number M08A

Typical Applications
1,2V-25V Adjustable Regulator

Fully Protected (Bulletproof)
Lamp Driver

Lamp Flasher
LM317L

2av
zaV.IUIIIA
INCANDESCENT

TL/H/9064-2

10k

TL/H/BOB4-\
Full output current not available at high input-output voltages

TL/H/B064-3
Output rate-4 flashes per second at 10% duty
cycle

tOptlonal-improves transient response
'Needed If device is more than 6 inches from
filter capacitors
ttVOUT

= 1.2SV (1 +

*) +

IADJ (R2l

1-144

r-

s:

Absolute Maximum Ratings

(0)

- 55·C to
Storage Temperature
Lead Temperature (Soldering, 4 seconds)

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.

+ 150·C
260·C

Output is Short Circuit Protected
ESD rating to be determined.

Power Dissipation
Internally Limited
Input-Output Voltage Differential
40V
Operating Junction Temperature Range -40·C to + 125·C

Electrical Characteristics (Note 1)
Parameter

Conditions

s:

Line Regulation

Tj = 25·C,3V

Load Regulation

Tj = 25'C, 5 mA

Thermal Regulation

Tj = 25·C, 10 ms Pulse

(VIN - VOUT)

s:

lOUT

s:

Min

s: 40V, IL s: 20 mA (Note 2)

IMAX, (Note 2)

Adjustment Pin Current
Adjustment Pin Current Change

5 mA s: IL s: 100 mA
3V s: (VIN - VOUT) s: 40V, P

3V s: (VIN - VOUT) s: 40V, (Note 3)
5 mA s: lOUT s: 100 mA, P s: 625 mW

Line Regulation

s: (VIN - VOUT) s: 40V, IL s: 20 mA (Note 2)
5 mA s: lOUT s: 100 mA, (Note 2)
TMIN s: Tj s: TMax
(VIN - VOUT) s: 40V
3V s: (VIN - VOUT) s: 15V
3V s: (VIN - VOUT) s: 13V

Load Regulation

Minimum Load Current
Current Limit

1.20

3V

(VIN - VOUT) = 40V

s: f s:

Max

Units

0.01

0.04

%/V

0.1

0.5

%

0.04

0.2

%/W

50

100

p.A

0.2

5

p.A

1.25

1.30

V

0.02

0.07

%IV

0.3

1.5

%

3.5
1.5

5
2.5

mA

200
50

300
150

mA
mA

s: 625 mW

Reference Voltage

Temperature Stability

Typ

Rms Output Noise, % of VOUT

Tj = 25·C, 10 Hz

Ripple Rejection Ratio

VOUT = 10V, f = 120 Hz, CADJ = 0
CADJ = 10p.F

%

0.65

100
25

10 kHz
66

0.003

%

65
80

dB
dB

Long-Term Stability

Tj = 125·C, 1000 Hours

0.3

Thermal Resistance
Junction to Ambient

Z Package 0.4" Leads
Z Package 0.125 Leads
50-8 Package

180
160
165

·C/W
·C/W
·C/W

165

·C/W

Thermal Rating of SO Package

1

%

Note 1: Unless otherwise noted, these specifications apply: -25'C ,;; Tj ,;; 125'C for the LM317L; VIN - VOUT ~ 5V and lOUT ~ 40 mAo Although power
disSipation is internafly IimHed, these specifications are applicable for power dissipations up to 625 mW. IMAX is 100 mAo
Note 2: Regulation is measured at constant junction temperature, using pulse testing with a low duty cycle. Changes in output voltage due to heating effects are
covered under the specification for thermaf regulation.
Note 3: Thermal resistance of the TO·92 package is 18fJ'C/W junction to ambient with 0.4" leads from a PC board and 16fJ'C/W junction to ambient with 0.125"
lead length to PC board.

1-145

.....
......

r-

~ ~-----------------------------------------------------------------------------

.........

C')

Typical Performance Characteristics (Output capacitor =

0 ,..F unless otherwise noted.)

:i
~

0.3

fi

...~

-0.1

~
!:;

-0.2

">
~
""

-0.3

IL' O.IA

--'-

'-

5

VIN"&V
VIOUY l V

~

l

-0.4

.-

0.2

-0.5

~

iii

10

I-++-+---I-~+--++-I

.....

...

1.250

ffi

..

~

1'.;

40
20

fff-

iD

~

60 I - - I - C >

....

40

~

"'

I
20

25

3D

20

I
I--I--I---

~Z

>1=

35

Line Transient Response

a" -D.5

T_

C7,,1F
tCAOJ'10"F t -

>G

~~

"~~...
8

TIME 11<.1

W 12

102

CL -0
CADJ'10"F

,
-- ,

CL-O
~~
1== CADJ"O
I--/

L" 1 I-tF

CADI' '0"'

./

IL=4DmA

« W

1-1- f--

10k

lOOk

10

1M

100

100
50

10k

lOOk

1M

Thermal Regulation

r..

1 1 11\l

~8~;R'~~W-

'1:;

VI),5J
VOUT= 'OV
INL" SmA

II

lk

30

1

-~~

-1.5 I-t-

VIN '15V
VOUT"'0V
IL ;;;40mA
Tlo 2S'C

FREQUENCY (Hz)

hL.'o
CAOJ=oxAT

0.5

-0.5

/

'0-2

lk

~

/--

"1\

Ti' 25'C

100

40

30

/

Load Transient Response
1.0

20

Output Impedance

1.&

-1.0

1 Ii

248

""
~~

j

-1.& I- j-Tr2~'C I
1.0
I I I
0.&
o

...
~~
~~

IL=4DmA

~C:::f

10

lNPUT·DUTPUT DIFFERENTIAL (VI

I
10

." "

if

-1.0 I- !-_.YOUT" 10V

... s
~~ii

1

o

FREQUENCY (Hz)

1.5

l\ 1 1
I- h IIN • 1
,5V

1

......

VIN·15V
VOUT"0V

OUTPUT VOLTAGE (VI

CL = 0
1.0 It/CAOJ=O
0.6

--

~ ~"2&'C-

Tj= _25°C

I - - +--C~OJ"O~F- I---

80

Ul

TliI25'jC-

1.0

-75 -50 -25 0 25 &0 75 100 125 150

'""z

f= 120 Hz

15

r

o

o

,,"
.....
~~

Ia

Ripple Rejection

VIN-VOUT= 5V
IL""40mA

10

~~

...B 2.0

I'r-.,

TEMPERATURE rCI

-r--

Ti= ~5'C I

v

~.

3.0

1.230

cAciJ' ld"F +-- +--

CAOJ' 0

II:

...

Minimum Operating Current

1.240

100

60

~

"'

TEMPERATURE rCI

C

Ripple Rejection

r-+-

-7& -50 -2& 0 2& &0 7& 100 125 1&0

40

..s'
...
~

TEMPERATURE rCI

fi
$

30

1.5

0.5 L-L-L-.l.-.l.-..1-..1-...1-...L.....J
-75 -50 -25 0 25 &0 75 100 125 150

iii

20

4.0

~~

1--1-=::++

ii

80

40

Reference Voltage
Temperature Stability

~,.26D

100

..a

l

INPUT·OUTPUT DIFFERENTIAL (VI

;;! 2.5 I-++--/'---I-~+--++-I

1.0

1/

4&

35
0

1.270

..'"

~5'C

a:
!1i

0

~O ~~~'-'-~'-'--r~

i

~ •-==

v~

50

z

Ti"2& C

y ..

Dropout Voltage

~

I

~

0.1

TEMPERATURE rCI

2.0

~

5&

...

""

-7& -50 -2& 0 2& 50 75 100 125 150

~

C

a

TI=2&'C

~
B
...

t-...

60

I

~

ill

Adjustment Current

Current Limit

Load Regulation
0.1

CL ='pF

CAOJ= 10"F

~ -30
z 1.5

T2~'CI

;
"

I I 1\
ITI
20

10

TIME 11<.1

30

40

i

""

...

1.0
0.5
0
10

20

30

40

TIME (m.1
TL/H/9064-6

1-146

Application Hints
In operation, the LM317L develops a nominal 1.25V reference voltage, VREF, between the output and adjustment terminal. The reference voltage is impressed across program
resistor R1 and, since the voltage is constant, a constant
current 11 then flows through the output set resistor R2, giving an output voltage of
VOUT = VREF (1

In general, the best type of capacitors to use is solid tantalum. Solid tantalum capacitors have low impedance even at
high frequencies. Depending upon capacitor construction, it
takes about 25 p.F in aluminum electrolytic to equal 1 p.F
solid tantalum at high frequencies. Ceramic capacitors are
also good at high frequencies; but some types have a large
decrease in capacitance at frequencies around 0.5 MHz.
For this reason, a 0.01 p.F disc may seem to work better
than a 0.1 p.F disc as a bypass.
Although the LM317L is stable with no output capacitors,
like any feedback Circuit, certain values of external capacitance can cause excessive ringing. This occurs with values
between 500 pF and 5000 pF. A 1 p.F solid tantalum (or 25
p.F aluminum electrolytic) on the output swamps this effect
and insures stability.

+ :~) + IADJ(R2)

Since the 100 p.A current from the adjustment terminal represents an error term, the LM317L was designed to minimize IADJ and make it very constant with line and load
changes. To do this, all quiescent operating current is returned to the output establishing a minimum load current
requirement. If there is insufficient load on the output, the
output will rise.

Load Regulation

LM317L

The LM317L is capable of providing extremely good load
regulation but a few precautions are needed to obtain maximum performance. The current set resistor connected between the adjustment terminal and the output terminal (usually 2400) should be tied directly to the output of the regulator rather than near the load. This eliminates line drops from
appearing effectively in series with the reference and degrading regulation. For example, a 15V regulator with O.05'!}
resistance between the regulator and load will have a load
regulation due to line resistance of O.OS,!} x IL. If the set
resistor is connected near the load the effective line resistance will be O.05'!} (1 + R2/R1) or in this case, 11.5 times
worse.
Figure 2 shows the effect of resistance between the regulator and 240'!} set resistor.

TLiH/9064-7

FIGURE 1

With the TO-92 package, it is easy to minimize the resistance from the case to the set resistor, by using two separate leads to the output pin. The ground of R2 can be returned near the ground of the load to provide remote ground
sensing and improve load regulation.

External Capacitors
An input bypass capacitor is recommended in case the regulator is more than 6 inches away from the usual large filter
capacitor. A 0.1 p.F disc or 1 p.F solid tantalum on the input
is suitable input bypassing for almost all applications. The
device is more sensitive to the absence of input bypassing
when adjustment or output capacitors are used, but the
above values will eliminate the possiblity of problems.
The adjustment terminal can be bypassed to ground on the
LM317L to improve ripple rejection and noise. This bypass
capacitor prevents ripple and noise from being amplified as
the output voltage is increased. With a 10 p.F bypass capacitor 80 dB ripple rejection is obtainable at any output level.
Increases over 10 p.F do not appreciably improve the ripple
rejection at frequencies above 120 Hz. If the bypass capacitor is used, it is sometimes necessary to include protection
diodes to prevent the capacitor from discharging through
internal low current paths and damaging the device.

LM317L

~ R1
~

240

TLiH/9064-8

FIGURE 2. Regulator with Line Resistance
in Output Lead

1-147

~~------------------------------------------------------~

.....
.....

CO)

:E
~

Application Hints (Continued)
vent the capacitors from discharging through low current
pOints into the regulator. Most 10 p.F capacitors have low
enough internal series resistance to deliver 20A spikes
when shorted. Although the surge is short, there is enough
energy to damage parts of the IC.
When an output capacitor is connected to a regulator and
the input is shorted, the output capacitor will discharge into
the output of the regulator. The discharge current depends
on the value of the capacitor, the output voltage of the regulator, and the rate of decrease of VIN. In the LM317L, this
discharge path is through a large junction that is able to
sustain a 2A surge with no problem. This is not true of other
types of positive regulators. For output capacitors of 25 p.F
or less, the LM317L's ballast resistors and output structure
limit the peak current to a low enough level so that there is
no need to use a protection diode.
The bypass capacitor on the adjustment terminal can discharge through a low current junction. Discharge occurs
when either the input or output is shorted. Internal to the
LM317L is a 50.0. resistor which limits the peak discharge
current. No protection is needed for output voltages of 25V
or less and 10 p.F capacitance. Figure 3 shows an LM317L
with protection diodes included for use with outputs greater
than 25V and high values of output capacitance.

Thermal Regulation
When power is dissipated in an IC, a temperature gradient
occurs across the IC chip affecting the individual IC circuit
components. With an IC regulator, this gradient can be especially severe since power dissipation is large. Thermal
regulation is the effect of these temperature gradients on
output voltage (in percentage output change) per watt of
power change in a specified time. Thermal regulation error
is independent of electrical regulation or temperature coefficient, and occurs within 5 ms to 50 ms after a change in
power dissipation. Thermal regulation depends on IC layout
as well as electrical design. The thermal regulation of a voltage regulator is defined as the percentage change of VOUT,
per watt, within the first 10 ms after a step of power is applied. The LM317L specification is 0.2%/W, maximum.
In the Thermal Regulation curve at the bottom of the Typical
Performance Characteristics page, a typical LM317L's output changes only 7 mV (or 0.07% of VOUT = -10V) when
a lW pulse is applied for 10 ms. This performance is thus
well inside the specification limit of 0.2%/W x lW = 0.2%
maximum. When the lW pulse is ended, the thermal regulation again shows a 7 mV change as the gradients across the
LM317L chip die out. Note that the load regulation error of
about 14 mV (0.14%) is additional to the thermal regulation
error.
Protection Diodes
When external capacitors are used with any IC regulator it is
sometimes necessary to add protection diodes to pre-

......
VIN -

Y

LM317L

VIN AOJVOUT IHt--"'--.l--_VOUT
02 .... -

lN4002~~

Rl
",,240

~

Cl

TL/H/9064-9

FIGURE 3. Regulator with Protection Diodes

VOUT

= 1.25V (1 + ~n

01 protects against C1

02 protects against C2

1-148

IADJ R2

en
n

:T
CD

3
~

n
C

~.

IN

Dl

H20

3

lOOk

n18
62V

H12
~

D.3

./>.
CD

n19
62V

H14
15k

H15
60k

OUT

TUH/9064-10

lH&Wl

Typical Applications (Continued)
Digitally Selected Outputs

High Gain Amplifier
v·

t---~P_VOUT

VIN-----of

.,

Rl
240

12

HI
10.

INPUT

--'N'II-+-""

INPUTS

TL/H/9064-12

TL/H/9064-11

'Sets maximum VOUT

Adjustable Current LImiter

Precision Current Limiter

TL/H/9064-13

12,; RI ,; 240
TUH/9064-14

Adjustable Regulator with
Improved Ripple Rejection

Slow Turn-On 15V Regulator
~,-

.........::r-....

_ _ _ _~~~~T
01*
IN400Z

IN40D2

CI
ZipF

TUH/9064-15

tSolid tantalum
'Discharges Cl il outpUl is shorted to ground

TLIH/9064-16

Adjustable Regulator with Current Limiter

High Stability 10V Regulator

r----"+

VIN
16Y

I
I
I
I

l
I

TRANSFORMER.

I
I
I
I

t-....--YOUT= 1.2S0Y (:- .,)
'--+--'

II

I :~~Tg~~:= I
I CAPACITOR I
I
I
I
I
I
I

R3
287
1%

I

I

R2

2.

R4- 2R3= 22

I

I

IL _____..a~1---4~~~

TLlH/9064-17

TL/H/9064-18

Short circuit current is approximately 600 mV IR3, or 60 mA (compared to
LM317LZ's 200 mA current limit).
At 25 mA oUlput only 3/4V of drop occurs in R3 and R4.

1·150

Typical Applications

(Continued)

OV-30V Regulator

Regulator With 15 mA Short Circuit
Current

lM3171
VIN
35V

Power Follower
10V-40V

VOUT

Cl

-=!=" O.lpF
lM395

INPUT

Rl
10k
OUTPUT

lM317l

R2
12

-10V
TLIH19064-20

TLIH/9064-19

TL/HI9064-21

Full output current not available at high input·out·
put voltages

Adjusting Multiple On-Card Regulators with Single Control·

J-+-VOUT

L..-_-..._____

---l _

I

____ __ J

• All outputs within

± 100 mV

tMinimum load -5mA

TL/HI9064-22

100 mA Current Regulator

1.2V -12V Regulator with Minimum
Program Current

50 mA Constant Current Battery
Charger for Nickel-Cadmium
Batteries
lM317l

15V

TlIHI9064-25

TLlH19064-23
'Minimum load current::::: 2 rnA

1-151

TUH/9064-24

~

.....
....

C')

:::::E
~

r-----------------------------------------------------------------------------,
Typical Applications (Continued)
5V Logic Regulator with Electronic Shutdown·

.....

Current Limited 6V Charger

.

VIN

1o-o4....-4t-~9UT

aVTO 30V

~--

C2
O.I~F

1000 "F··

.........'V\j"'""-TTL
Ik

RI
10·
TL/H/S084-26

'Minimum output'" 1.2V
TL/H/S0B4-27

'Sets peak currenl, IpEAK - O.By/RI
"1000 ,.F Is recommended 10 flltar aut any Inpullranslants.

Short Circuit Protected BOV Supply
TRIAD
BLACK Faox GREEN

l1&~~II~~
I,'IB AMP, TYPE BAO
FUSE OR CIRCUIT BREAKER

BLACK·YELLOW

I

oJ

33V

IW

.....-+__..._
~~---'

BOVDC

OmAT020mA

TL/H/9064-2B

1·152

r-

Typical Applications

s:::

...........
Co)

(Continued)

r-

Basic High Voltage Regulator
Y,N ~170V_t-----_....- . ,

R3

100
112W

VOUT

lM317l

VOUT
TO

~~p----,,-1.2V

160V@25mA

ADJ

D2
IN4DDI

R6
20k
5W

R4

10D
01, 02: NSD134 or similar
Cl, C2: 1 f'F, 200V mylar"
·Heat sink

Cl
T'·DI'F

TL/H/9064-29

Precision High Voltage Regulator
V,N;:::170V _ ....- -_ _ _..._ ..

R3

100
1/2W
lM317l
AOJ

VOUT

VOUT~""-~-~--4~BVTO
16DV@25mA
RB

2.7
R6
lk

*

C2
0 I'F

T1.

R5
Uk

D2
lN4DDI

R7
2Dk
5W

Cl

01,02: NSD134 arsimilar --r-1.DI'F
Cl, C2: 1 f'F, 200V mylar"
"Heat sink
UMylar is a registered trademark of DuPont Co.

1-153

TL/H/9064-30

•

Typical Applications (Continued)
Tracking Regulator

Regulator With Trlmmable Output Voltage

VIN

vIN (25V TO 40V)
........._

...-VOUT

VOUT (22V ±I%)

RI
10k'

R2

10k'

R5
16k
5%

rr
it..
_~._ ..

GNO

I ~F TANTALUM

TL/H/9064-32

Trim Procedure:

-

If VOUT is 23.0BV or higher, cut out R3 Of lower, don't cut it out).

-

Then if VOUT is 22.47V or higher, cut out R4 (If lower, don't).

-

Then if VOUT Is 22.16V or higher, cut out RS (H lower, don't).

This will trim the output to well within ± 1 % of 22.00 Vee, wHhout any of the
expense or uncertainty of a trim pot (see LB·46). Of course, this technique
can be used at any output voltage level.

TL/H/s064-31

AI = LM301 A, LM307, or LF13741 only
Rl, R2 = matched resistors with good Te tracking

Precision Reference with Short-Circuit Proof Output
15V----~----------------------~----_,

IO.OOOV OUTPUT

1 ppmfC MAX

R2

2k'

r

I
I

I

I

I

L
lk CERMET
OUTPUT ADJUST
OUTPUT

POWER

COMMON----~--------~~------------~~--------~

RETURN
TL/H/9064-33

'Rl-R4 from thin·fllm network,
Beckman 694·3·R2K·D or similar

1-154

~National

~ Semiconductor

lM320l, LM79LXXAC Series
3 TerminallNegative Regulators
m

General Description
The LM320LlLM79LXXAC series of 3-terminal negative
voltage regulators features fixed output voltages of -5V,
-12V, and -15V with output current capabilities in excess
of 100 mAo These devices were designed using the latest
computer techniques for optimizing the packaged IC thermal/electrical performance. The LM79LXXAC series, even
when combined with a minimum output compensation capacitor of 0.1 fl-F, exhibits an excellent transient response, a
maximum line regulation of 0.07% VolV, and a maximum
load regulation of 0.Q1 % Vo/mA.
The LM320LlLM79LXXAC series also includes, as self-protection circuitry: safe operating area circuitry for output transistor power dissipation limiting, a temperature independent
short circuit current limit for peak output current limiting, and
a thermal shutdown circuit to prevent excessive junction
temperature. Although designed primarily as fixed voltage
regulators, these devices may be combined with simple external circuitry for boosted and/or adjustable voltages and
currents. The LM79LXXAC series is available in the 3-lead
TO-92 package, and SO-8; 8 lead package. The LM320L
series is available in the 3-lead TO-92 package.

Typical Applications

For output voltage other than -5V, -12V and -15V the
LM137L series provides an output voltage range from 1.2V
to 47V.

Features
iii Preset output voltage error is less than ±5% overload,

line and temperature
III Specified at an output current of 100 mA
III Easily compensated with a small 0.1 fl-F output
capacitor
1111 Internal short-circuit, thermal and safe operating area
protection
(;I Easily adjustable to higher output voltages
iii Maximum line regulation less than 0.07% VOUTIV
III Maximum load regulation less than 0.01 % VouT/mA

Connection Diagrams

Fixed Output Regulator

SO-8 Plastic (Narrow Body)
1·

8

-VIN

2

7

-VIN

-VIN

3

6

-VIN

NC

4

5

GND

-VOUT

-VINo--+---I

LM320L2
LM79LXXACZ

NC

TL/H/774B-4
TUH/774B-l

'Required if Ihe regulalor is localed far from Ihe power supply filler. A 1 f'F
aluminum electrolytic may be substituted.
"Required for slability. A 1 f'F aluminum electrolytic may be subsliMed.

Adjustable Output Regulator

Cl

Top View
Order Number LM79L05ACM,
LM79L12ACM or LM79L 15ACM
See NS Package Number M08A

TO·92 Plastic Package (Z)

+

O.33~F

Rl

TL/H/774B-2

Bottom View

t - - + - -...-o -VO
TL/H/774B-3

-vo = -SV - (SVlR1 + 10). R2.
SV/RI > 310
1-155

Order Number LM320LZ·5.0, LM79L05ACZ,
LM320LZ·12, LM79L 12ACZ, LM320LZ·15 or
LM79L15ACZ
See NS Package Number Z03A

Absolute Maximum Ratings
If Military/Aerospace speclfled devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Vo = -5V, -12V, -15V
-35V
Internal Power Dissipation (Note 1)
Internally Limited

Electrical Characteristics (Note 2) TA =

-5V

-12V

-15V

Input Voltage (unless otherwise noted)

-10V

-17V

-20V

Parameter

Conditions

1 mA ~ 10 ~ 100 mA
VMIN ~ VIN ~ VMAX
1 mA ~ 10 ~ 40 mA
VMIN ~ VIN ~ VMAX
Line Regulation

Tj = 25·C
1 mA ~ 10

Load Regulation

~

-5

-5.25
(-20 ~ VIN

~

(-20

VIN

~

VIN

Long Term Stability

10 = 100mA

20

Quiescent Current

10 = 100mA

2

t..la

Quiescent Current
Change

1 mA

~

-4.75 -12.6
-7.5) (-27 ~ VIN

~

VIN

60
-7) (-27

~

VIN

Vn

Output Noise Voltage Tj = 25·C, 10 = 100 mA
f = 10 Hz - 10 kHz

t..VIN
t..Vo

Ripple Rejection

Tj = 25·C, 10 = 100 mA
f=120Hz

Input Voltage
Required to
Maintain Line
Regulation

Tj = 25·C,lo = 100 mA
10 = 40mA

~

45
-14.6) (-30

~

~

45
-14.5) (-30

~

VIN

~

~

VIN

~

45
-17.7)

mV
V

VIN

~

45
-17.5)

mV
V

125

mV

6

mVlkhrs

2

6

0.3

0.3

0.3

0.1

0.1

0.1

0.25

-7.5) (-27

40

~

VIN

~

-14.8) (-30

96

50

~

VIN

~

mA
V
/LV
dB

-17.7
-17.5

Z package is 60"C/W Ole, 23Z'C/W 0ja al still air, and 88'C/W al400 fIImin of a~. The M package OJ. is 180"C/W in stili air.

The maximum junction temperature shall not exceed 125°C on electrical parameters.
Note 2: To ensure constanl junction lemperalure, low duty cycle pulse lesting is used.

1-156

mA

0.25

50
-14.6
-14.5

mA

-18)

120

52
-7.3
-7.0

V

-14.25
-17.5)

60

2

0.25
~

-11.4 -15.75
-14.25
-14.8) (-30 ~ VIN ~ -18)

48

1mA~lo~40mA

(-20

I Typ I Max

Min

100

6

10 = 100mA

Note 1: Thermal resistance of

~

~

~

Units

-11.5 -15.6 -15 -14.4

-12.6 -11.4 -15.75
~ VIN ~ -14.5) (-30 ~ VIN

60
-7.3) (-27

100 mA

VMIN ~ VIN ~ VMAX

-12

50

10

10

~

100 mA

t..Vo

~

I Typ I Max

Min

-4.8 -12.5

-5.25
-4.75
(-20 ~ VIN ~ -7) (-27

Tj = 25·C, 10 = 100 mA
(-20
VMIN ~ VIN ~ VMAX
Tj = 25·C, 10 = 40 mA
VMIN ~ VIN ~ VMAX

I:..vo

ITyp I Max

Min

Tj = 25·C,lo = 100 mA -5.2

Output Voltage

I:..vO

O·C to + 70·C unless otherwise noted.

Output Voltage

Symbol
Vo

O·Cto +70·C
+ 125·C
- 55·C to + 1500C
2600C

Operating Temperature Range
Maximum Junction Temperature
Storage Temperature Range
Lead Temperature (Soldering, 10 sec.)

V
V

Typical Performance Characteristics
1

Maximum Average Power
Dissipation (TO-92)

-

a.7

!

Iiii!I

0.4

..

D.2

g
I

t--

a.l

a

a.121" LEAD LENGTH
FRDM PC BOARD
FREE AIR

11

3D

5
~
~

..

~,

41

~

II

..
..~

"

0.01

o

7&

o

I
~

-1.&
-1

a

~

i

10

5
~
~

.
;..

~~

TI"Z1i'C

0.1

11

20

21

TI"2I'C

0.1

!;

~

TJ'2S'C

1- ~

0.11

VOUT' -12V

ID~~ ~ r-

VOUT'-IV

'G'4amA /
'O'DmA

1'111..
r--.. ~ ~

"

o

3D

o

-I -10 -11 -20 -21 -30 -31
INPUT VDLTAOE (VI

Output Voltage VB.
Temperature (Normalized
to 1V@

Ripple Re/ectlon
10

AVDUT"UD mV

VOUT'OV

0.05

INPUT-OUTPUT DIFFERENTIAL (VI

Dropout Voltage
-IIV AND -IIV

=~

0.2

TJ'2~'C

TJ'~C

0.11

TA - AMI1ENT TEMPERATURE ('CI

-2

0.2&

AVOUT • IUD mV
D.2

::--...

0.4" LEAD LENGTH
FRDMPM~A~~-

Short Circuit Output
Current

Peak Output Current

UI

1.010 .....---.---.""':"...,..-...,..-..,

,

AVDU;"oa~V
-2

lD"UDmA
'0'4amA_
-IV 1//I'G'OmA

_

V\r.-V~UT·"'V
4 IN'7

-1.1
-1

p'~III]i

10UT'I~t

o

II

10

71

IUD

o T~;,~C

121

10

TJ -JUNCTIGN TEMPERATURE ('Cl

3

lGO

III1IM

D.aaa L-......I_...L_-1._...,L;;

10

VOUT'-IV
V,N' -IDV
'OUT'IDmA
TA'2I'C

TJ'~C

~

TJ'2I'C

..!!::.

TJ"2S'C

-I

I

-10

-11

11

rn

m

=:±~O'~
CO".F I
ALUMINU~~

I
j

"

Output Impedance

I
f--

ZIi

TI - JUNCTION TEMPERATURE ('C)

Quiescent Current

1

o

lOOk

lk
10k
FREQUENCY (Hz)

/
1- VOUT'-IV 101" 40
-10 -25

t-

0.01

-3D -35

10

INPUT VOLTAGE (V)

loa

lk

10k

lOOk

1M

FREQUENCY (H.I
TL/H17748-5

Typical Applications (Continued)
± 15V, 100 mA Dual Power Supply

1--...-oVOUT· 15V@ 100 mA
C2
0.1 ~F
GNDo-~------~----~,-O

C4

0.1

-VINO~"'--I
20V

~F

I-~"'O-VOUT =-15V@ 100 mA
TL/H/7748-6

1-157

Schematic Diagrams
-5V
GND

TL/H/774B-9

-12Vand -15V
GND

R21

4.21>

R22

R23
0.&
(7.4)
-VIN

TL/HI774B-1D

1-158

~National

~ Semiconductor

LM337L 3-Terminal Adjustable Regulator
General Description
The LM337L is an adjustable 3-terminal negative voltage
regulator capable of supplying 100 mA over a 1.2V to 37V
output range. It is exceptionally easy to use and requires
only two external resistors to set the output voltage. Furthermore, both line and load regulation are better than standard fixed regulators. Also, the LM337L is packaged in a
standard TO-92 transistor package which is easy to use.
In addition to higher performance than fixed regulators, the
LM337L offers full overload protection. Included on the chip
are current limit, thermal overload protection and safe area
protection. All overload protection cirCUitry remains fully
functional even if the adjustment terminal is disconnected.
Normally, only a single 1 p.F solid tantalum output capacitor
is needed unless the device is situated more than 6 inches
from the input filter capaCitors, in which case an input bypass is needed. A larger output capacitor can be added to
improve transient response. The adjustment terminal can be
bypassed to achieve very high ripple rejection ratios which
are difficult to achieve with standard 3-terminal regulators.
Besides replacing fixed regulators, the LM337L is useful in a
wide variety of other applications. Since the regulator is
"floating" and sees only the input-to-output differential voltage, supplies of several hundred volts can be regulated as
long as the maximum input-to-output differential is not exceeded.
Also, it makes an especially simple adjustable switching regulator, a programmable output regulator, or by connecting a
fixed resistor between the adjustment and output, the
LM337L can be used as a precision current regulator. Supplies with electronic shutdown can be achieved by clamping
the adjustment terminal to ground which programs the output to 1.2V where most loads draw little current.

The LM337L is available in a standard TO-92 transistor
package and a 50-8 surface mount package. The LM337L
is rated for operation over a - 25'C to + 125'C range.
For applications requiring greater output current in excess
of 0.5A and 1.5A, see LM137 series data sheets. For the
positive complement, see series LM117 and LM317L data
sheets.

Features
• Adjustable output down to 1.2V
III Guaranteed 100 mA output current
iii Line regulation typically 0.01 %N
III Load regulation typically 0.1 %
II Current limit constant with temperature
III Eliminates the need to stock many voltages
• Standard 3-lead transistor package
• 80 dB ripple rejection
II Output is short circuit protected

Connection Diagram

v:: ~o:
V,N

TLlH/9134-1

3

6

ADJ 4

v,N
V,N

5

Bottom View

TLIH/9134-2

Top View
Order Number LM337LM or LM337LZ
See NS Package Number M08A or Z03A

Typical Applications
1.2V-2SV Adjustable Regulator

Regulator with Trimmable Output Voltage

+ lpF
RS

16k.n

SOLID
TANTALUM

5%
!-=-::.;.....~---------4>---22V

TL/H/9134-3

Full output current not available at high input·output voltages
-VOUT

~

-1.2SV (1

+~)
240n

TL/H19134-4

Trim Procedure:
-If VOUT is - 23.0eV or bigger, cut out R3 (if smaller, don't cut it out).

tel ~ 1 fLF solid tantalum or 10 fLF aluminum electrolytic
required for stability

·C2 = 1 J.LF solid tantalum is required only if regulator is more
than 411 from power supply filter capaCitor

-Then if VOUT is - 22.47V or bigger, cut out R4 (if smaller, don't).
-Then if VOUT is -22.16V or bigger, cut out RS (if smaller, don't).
This will trim the output to well within 1% of -22.00 Voc, without any of the
expense or trouble of a trim pot (see LB·46). 01 course, this technique can
be used at any output voltage level.

1-159

•

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Power Dissipation
Internally Limited
Input-Output Voltage Differential
40V

Operating Junction Temperature Range - 25·C to
- 55·C to
Storage Temperature
Lead Temperature (Soldering, 10 sec.)
Plastic Package (Soldering 4 sec.)
ESD rating to be determined.

+ 125·C
+ 150·C
300·C
260·C

Electrical Characteristics (Note 1)
Parameter

Conditions

Min

Typ

Max

Units

Line Regulation

TA = 25·C,3V:S: IV,N - vOUTI :s: 40V,
(Note 2)

0.Q1

0.04

%N

Load Regulation

TA = 25·C, 5 mA :S: lOUT :S: 'MAX, (Note 2)

0.1

0.5

%

Thermal Regulation

TA

0.04

0.2

%/W

50

100

poA

0.2

5

poA

1.25

1.30

V

0.02

0.07

%N

0.3

1.5

%

3.5
2.2

5
3.5

mA
mA

200
50

320
120

mA
mA

= 25·C, 10 ms Pulse

Adjustment Pin Current
Adjustment Pin Current Change

5 mA:S: IL :S: 100 mA
3V :S: IV,N - vOUTI :S: 40V

Reference Voltage

3V :S: IV,N - vOUTI :S: 40V, (Note 3)
10 mA:S: lOUT :S: 100 mA, P :S: 625 mW

Line Regulation

3V :S: IV,N - vOUTI :S: 40V, (Note 2)

Load Regulation

5 mA :S: lOUT

Temperature Stability

TMIN

Minimum Load Current

IV,N - vOUTI s: 40V
3V s: IV,N - vOUTI s: 15V

Current Limit

3V s: IV,N - vOUTI s: 13V
IV,N - vOUTI = 40V

Rms Output Noise, % of VOUT

= 25·C, 10 Hz s: f s: 10 kHz
VOUT = -10V, F = 120 Hz, CADJ = 0
CADJ = 10 poF
TA = 125·C

Ripple Rejection Ratio
Long·Term Stability

s:

1.20

100 mA, (Note 2)

s: TJ s: TMAX

0.65

100
25

TA

66

%

0.003

%

65
80

dB
dB

0.3

1

%

Note 1: Unless otherwise specified. these specifications apply -25'C 0: T, 0: + 125'C for the LM337L; IViN - vOUTI = 5V and lOUT = 40 mAo Although power
dissipation Is Internally limited, these specifications are applicable for power dissipations up to 625 mW. IMAX Is 100 mAo
Note 2: Regulation Is measured at constant lunctlon temperature, using pulse testing with a low duly cycle. Changes In output voltage due to heating effects are
covered under the specHlcatlon for thermal regulation.
Note 3: Thermal resistance of the TO·92 package Is 180'CIW lunctlon to ambient with 0.4' leads from a PC board and 160'C/W junction to ambient with 0.125'
lead length to PC board. The M package 9JA I. 180'C/W In still air.

1-160

,-------------------------------------------------------------------------, r

==

~National

Co)

01:00

-a.
tJ)

.m'

~ Semiconductor

CD

LM341, LM78MXX Series
3-Terminal Positive Voltage Regulators
General Description

Features

The LM341 and LM78MXX series of three-terminal positive
voltage regulators employ built-in current limiting, thermal
shutdown, and safe-operating area protection which makes
them virtually immune to damage from output overloads.

•
•
•
•
•
•
•

With adequate heatsinking, they can deliver in excess of
O.5A output current. Typical applications would include local
(on-card) regulators which can eliminate the noise and degraded performance associated with single-point regulation.

Output current in excess of O.5A
No external components
Internal thermal overload protection
Internal short circuit current-limiting
Output transistor safe-area compensation
Available in TO-220, TO-39 and TO-202 packages
Output voltages of 5V, 6V, 8V, 12V, 15V, and 24V

Connection Diagrams
TO-202(P)
Plastic Package

TO-39 Metal Can Package (H)

o
INPUT

TL/H/10484-5

INPUT

Bottom View
Order Number LM78MOSCH, LM78M06CH, LM78M08CH,
LM78M12CH, LM78M1SCH or LM78M24CH
See NS Package Number H03B

GND

TLlH/104B4-2

Order Number LM341P-S.0, LM341P-12 or LM341P-1S
See NS Package Number P03A

II

TO-220 Power Package (T)

TL/H/10484-B

Top View
Order Number LM78MOSCT, LM78M06CT, LM78M08CT,
LM78M12CT, LM78M1SCT, LM78M24CT,
LM341T-5.0, LM341T-12 or LM341T-1S
See NS Package Number T03B

DUAL MARKING: The LM341T·5.0 and the LM78MOSCT parts are "dual marked" (these parts are marked with both part
numbers) because they have the same specifications. The same is true for the LM341T·12/LM78M12CT and the
LM341T-1S/LM78M1SCT part number sets.

H61

Absolute Maximum Ratings

(Note 1)

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.

Operating Junction Temperature Range - 40·C to + 125·C

Storage Temperature Range

-65·C to + 150"C

Lead Temperature (Soldering, 10 seconds)
TO·39 Package (H)
TO·220 Package (T)
TO·202 Package (P)

Input Voltage
5V,,;. Vo";' 15V
Vo = 24V

35V
40V

ESD Susceptibility

TBD

Power Dissipation (Note 2)

300·C
260·C
230·C

Internally Limited

Electrical Characteristics
Limits in standard typelace are lor TJ = 25·C, and limits in boldface type apply over the -40"C to +125·C operating
temperature range. Limits are guaranteed by production testing or correlation techniques using standard Statistical Quality
Control (SQC) methods.

LM341-5.0, LM78M05C Unless otherwise specilied: VIN =
Symbol
Vo

Parameter
Output Voltage

10V, CIN = 0.33 p.F, Co = 0.1 p.F

Conditions
IL = 500 mA
5 mA :s; IL ,,;. 500 mA
PD ,,;. 7.5W,7.5V :s; VIN ,,;. 20V

VR LINE

Line Regulation

7.2V:s; VIN ,,;. 25V

VRLOAD

Load Regulation

5 mA ,,;. IL ,,;. 500 mA

10

Quiescent Current

IL = 500mA

Ala

Quiescent Current Change

I
I

Min

Typ

Max

4.8

5.0

5.2

4.75

5.0

5.25

V

IL = 100mA

50

IL = 500mA

100

10.0

5 mA ,,;. IL ,,;. 500 mA

0.5

7.5V ,,;. VIN ,,;. 25V, IL = 500 mA

1.0

Output Noise Voltage

1= 10 Hz to 100 kHz

AVIN

Ripple Rejection

I = 120 Hz, IL = 500 mA

VIN

Input Voltage Required
to Maintain Line Regulation

IL = 500mA

AVo

Long Term Stability

IL = 500mA

AVO

mA

40

p.V

78

dB

7.2

V

20

1·162

mV

100
4

Vn

Units

mV/khrs

Electrical Characteristics
Limits in standard typelace are lor TJ = 25'C. and limits in boldface type apply over the -40'C to + 125'C operating
temperature range. Limits are guaranteed by production testing or correlation techniques using standard Statistical Quality
Control (SQC) methods. (Continued)

LM78M06C
Symbol
Vo

VRLINE

VRLOAD

Unless otherwise specified: VIN = 11V. CIN = 0.33 p.F. Co = 0.1 p.F
Parameter

Output Voltage

Line Regulation

Load Regulation

Min

Typ

Max

IL = 350 mA

Conditions

5.75

6.0

6.25

5 mA s: IL s: 350 mA
BV s: VIN s: 21V

5.7

6.0

6.3

s: VIN s: 20V. IL =
s: VIN s: 25V. IL =
5 mA s: IL s: 200 mA
5 mA s: IL s: 500 mA

V

9V

200 mA

1.5

50

BV

200 mA

5

100

10

60

20

120

la

Quiescent Current

IL = 350mA

ala

Quiescent Current Change

5 mA

s: IL s: 350 mA
9V s: VIN s: 25V. IL =

4.5

Output Noise Voltage

1= 10 Hz to 100 kHz

Ripple Rejection

1= 2400 Hz.IL = 125 mA

VIN

Input Vol1age Required
to Maintain Line Regulation

IL = 350 mA
VIN = 35V

los

Output Short Circuit Current
Output Peak Current

aVo
aT

Average Temperature Coefficient
01 Output Voltage

mA

0.8

200 mA

aVIN
aVo

mV

B.O

0.5

Vn

IpK

Units

59

45

p.V

BO

dB

Vo+ 2

V

270

mA

700
IL = 5mA

0.5

mV/'C

•
1-163

Electrical Characteristics

Limits in standard typeface are for TJ = 25·C, and limits in boldface type apply over the -40·C to + 125·C operating
temperature range. Limits are guaranteed by production testing or correlation techniques using standard Statistical Quality
Control (SQC) methods. (Continued)

LM78M08C Unless otherwise specified: VIN =
Symbol
Vo

VR LINE

14V, CIN = 0.33 ".F, Co = 0.1 ".F

Parameter
Output Voltage

Line Regulation

Min

Typ

Max

IL = 350mA

Conditions

7.7

8.0

8.3

5 mA :5: IL :5: 350 mA
10.5V :5: VIN :5: 23V

7.6

8.0

8.4

V

11V:5: VIN :5: 20V,IL = 200 mA

2

50

10.5V :5: VIN :5: 25V, IL = 200 mA

6

100

10

80
160

VRLOAD

Load Regulation

5mA:5: 'L:5: 200mA
5mA:5: 'L:5: 500mA

25

10

Quiescent Current

IL = 350mA

4.6

ala

Quiescent Current Change

5 mA :5: IL :5: 350 mA

0.5

10.5V :5: VIN :5: 25V,IL = 200 mA

0.8

Vn

Output Noise Voltage

f = 10 Hz to 100 kHz

aVIN
aVo

Ripple Rejection

f = 2400 HZ,IL = 125 mA

VIN

Input Voltage Required
to Maintain Line Regulation

IL = 350mA
VIN = 35V

los

Output Short Circuit Current

IpK

Output Peak Current

aVo
aT

Average Temperature Coefficient
of Output Voltage

Units

56

mV

8.0
mA

52

".V

80

dB

Vo

+2

250

V

mA

700
IL = 5mA

0.5

1-164

mVl·C

Electrical Characteristics

Limits in standard typeface are for TJ = 25'C. and limits in boldface type apply over the -40'C to + 125'C operating
temperature range. Limits are guaranteed by production testing or correlation techniques using standard Statistical Quality
Control (SQC) methods. (Continued)

LM341-12, LM78M12C Unless otherwise specified: VIN =
Symbol
Vo

VRLlNE

Min

Typ

Max

IL = 500 rnA

11.5

12

12.5

5 rnA ,;;; IL ,;;; 500 rnA
Po';;; 7.5W. 14.8V ,;;; VIN ,;;; 27V

11.4

12

12.6

Parameter
Output Voltage

Line Regulation

19V. CIN = 0.33 /LF. Co = 0.1 /LF

Conditions

I
I

14.5V ,;;; VIN ,;;; 30V

V

IL= 100 rnA

120

IL = 500 rnA

240

VRLOAO

Load Regulation

la

Quiescent Current

IL = 500 rnA

Ala

Quiescent Current Change

5 rnA ,;;; IL ,;;; 500 rnA

0.5

14.8V ,;;; VIN ,;;; 30V.IL = 500 rnA

1.0

5 rnA ,;;; IL ,;;; 500 rnA
4

Output Noise Voltage

f = 10 Hz to 100 kHz

AVIN

Ripple Rejection

f = 120 Hz.IL = 500 rnA

VIN

Input Voltage Required
to Maintain Line Regulation

IL = 500 rnA

AVo

Long Term Stability

IL = 500 rnA

AVo

Parameter
Output Voltage

Line Regulation

Conditions
IL= 500 rnA

17.6V ,;;; VIN ,;;; 30V

75

/LV

71

dB
V

48

mV/khrs

Units

Min

Typ

Max

14.4

15

15.6

14.25

15

15.75

V

I IL = 100 rnA
I IL = 500 rnA

150
300

5mA,;;; IL';;; 500mA

VRLOAO
la

Quiescent Current

IL = 500 rnA

Ala

Quiescent Current Change

5 rnA ,;;; IL ,;;; 500 rnA

0.5

18V,;;; VIN ,;;; 30V.IL = 500 rnA

1.0

4

Output Noise Voltage

f = 10 Hz to 100 kHz

AVIN

Ripple Rejection

f = 120Hz, IL = 500 rnA

VIN

Input Voltage Required
to Maintain Line Regulation

IL = 500 rnA

AVo

Long Term Stability

IL = 500 rnA

AVo

10.0
rnA

90

/LV

69

dB

17.6

V

80

1·165

mV

300

Load Regulation

Vn

rnA

23V. CIN = 0.33 /LF. Co = 0.1 /LF

5mA,;;; IL';;; 500 rnA
Po';;; 7.5W.18V';;; VIN ,;;; 30V
VR LINE

10.0

14.5

LM341-15, LM78M 15C Unless otherwise specified: VIN =
Symbol

mV

240

Vn

Vo

Units

mVlkhrs

•

Electrical Characteristics
Limits in standard typelace are lor T J = 2S·C, and limits in boldface type apply over the - 40·C to + 12S·C operating
temperature range. Limits are guaranteed by production testing or correlation techniques using standard Statistical Quality
Control (SQC) methods. (Continued)

LM78M24C Unless otherwise specilied: VIN =
Symbol
Vo

VR LINE

33V, CIN = 0.33 p.F, Co = 0.1 p.F

Parameter
Output Voltage

Line Regulation

Min

Typ

Max

IL = 3S0mA

Conditions

23.0

24.0

2S.0

SmA :5: IL :5: 3S0 mA
27V :5: VIN :5: 38V

22.8

24.0

25.2

V

2BV :5: VIN :5: 36V, IL = 200 mA

S

SO

27V :5: VIN :5: 38V, IL = 200 mA

10

100

SmA:5: IL:5: 200mA

10

240
480

VRLOAD

Load Regulation

S mA :5: IL :5: SOO mA

30

IQ

Quiescent Current

IL = 3S0mA

S.O

~IQ

Quiescent Current Change

SmA :5: IL :5: 3S0 mA

0.5

27V:5: VIN:5: 38V, IL = 200 mA

0.8

Vn

Output Noise Voltage

1= 10Hzto 100 kHz

~VIN

Ripple Rejection

1= 2400 Hz, IL = 12S mA,
VIN = 30V

VIN

Input Voltage Required
to Maintain Line Regulation

IL = 3S0 mA

VIN = 35V

~VO

los

Output Short Circuit Current

IpK

Output Peak Current

~VO

Average Temperature Coefficient
01 Output Voltage

~T

Units

SO

mV

B.O
mA

170

p.V

70

dB

Vo+ 2

V

240

mA

700
IL = SmA

1.2

mvrc

Note 1: Absolute maximum ratings indicate limits beyond which damage to the component may occur. Electrical specifications do not apply when operating the
device outside of its rated operating condnions.
Note 2: The typical thermal resistance of the three package types is:
T (T0-220) package: 9(J.A) = 60 'C/W. 9(J.c) = 5 'C/W
P (TO·202) package: 9(J.A) = 70 'C/W. 9(J.c) = 12 'C/W
H (T0-39) package: 9(J.A) = 120 'C/W, 9(J.c) = 18 'C/W

1-166

r-----------------------------------------------------------------------------~

Schematic Diagram

r

:s::
.....
""en
CD

Co)

.---9-----...- - - - - - - - -....- - - - -....---1K>

VIN

::::!.

m

Q13

R13
830

R4

1.2k

~-~-~--~~-~-~-. .--~--. .-~---. .~GND
TL/H/10484-1

1·167

Typical Performance Characteristics
Peak Output Current

Ripple Rejection

1.50

3

~
a

~

100

,.25f--iJ=~

rr

1.00

~

.........;

TJ II25 0 C

0.75

rI

I I

0

0.25
0
0

5

S!

.......

~

"

i"

60

B

I""

_TJ"'50~

0.50

z

~

Jp~:~~I~V

80 ~

'at

40

~
Ii!

~
~

10

2.0

1.5

UT

i!

20

15

25

TJ" 25 0 C
50

30

10

100

0
0

50

0

lOOk

l!J

~
!i!

~
"EI

-

I"""-

0

r-

75

100

i

1.010
1.005
1.000
0.995
0.990

-

JUNCTION TEMPERATURE (Oc)

~

.5

4.0

§
"u

S
5

3.5

~

5.5

I
10

Ia

5.0

"-

i'...

~

4.0

4.5

ffi

-

20

5
25

50

75

100

125

L...- l -I--

r

25

~

3.5
3.0
5

150

10

JUNCTION TEMPERATURE (Oc)

15

20

25

30

35

INPUT VOLTAGE (v)

Output Impedance
10

V,N " 10V

Your lit ~w

....... .......

15

VOUT " 5V
louT=5mA
TJ a25 DC

.5

.......

Quiescent Current

4.5

I
5

Quiescent Current

MB5

0.975
0

150

12V
15V

6.0

§l 0.9BO

125

!mu.
5V

OUTPUT VOLTAGE (v)

Output Voltage (Normalized
to 1V at TJ = 2S0C)

:E

"V~T" I~OmV
25

10k

lk

FREQUENCY (Hz)

~500~A

'OUT io,Di A
I ~

Y,N

~

60_ 23V

Ii!

1.015

-+-

0.5

-

~

~~"'=VgHL:: Voc + 3.5Vrml

•

70

~

....

r---

TJ I: 25°C

~

0

10

1.0

~

z

0

~~

20

1"120Hz
Y,N - VOUT " 8 VDC
+3.5Vrml
loUT" 500 mA

BO

~

111111111

Dropout Voltage

:E

'at

Illor

INPUT-OUTPUT DIFFERENTIAL (v)

2.5

Ripple Rejection
90

S

i

.......

1.0

......,

loUT a 250 mA
T = 25 0 C
~

0.1

a!

3.0

~

VIN 1I10V

0

Your = 5Y

'"

0.01

lOUT" 5 mA
0.001
10

0
0

25

50

75

100

125

150

JUNCTION TEMPERATURE (Oc)

100

lk

10k

lOOk

1M

FREQUENCY (Hz)
TL/H/l0484-4

1-168

Typical Performance Characteristics

(Continued)

Line Transient Response
40

>'
..5
z
0
;::

...s:

'"

30

I I

Load Transient Response

LM7BMOS

INPUT VOLTAGE

......'"'"
-'
0

...>

1o

20

::::>

...
0-

::::>
0

0

S

OUTPUT VOLTAGE
DEVIATION

-10 TJ = 2SoC
10 = SOO rnA
Vo = S.OV
-20
o 2 4

~

1S

Q

10

4.0

20

o

z

VI
3.0 Vo

=10V
=S.OV

~
~

......'"'"

2.0

......'"'"
>
...
...

0

...
>

-'
0

::::>
0-

;;=

1.0
0

0-

0.5

I I
I

VOLTAGE
-r- ~UTPUT
DEVIATION

l"-

lL

::::>

::::>

1.0

I I

Q

-'

Ud7BMOS

LOAD CURRENT

0

~

I I

I L

-1.0

0

-2.0
10

12

o

10

TIME (1'.)

20

30

40

SO

60

TIME (I's)
TL/H/l0484-7

TUH/l04B4-B

Design Considerations

Typical Application

The LM78MXX/LM341 XX fixed voltage regulator series has
built-in thermal overload protection which prevents the device from being damaged due to excessive junction temperature.

0.33;~

The regulators also contain internal short-circuit protection
which limits the maximum output current, and safe-area protection for the pass transistor which reduces the short-circuit current as the voltage across the pass transistor is increased.

IN

OUT
Lt.t78MXX
LM341P-XX

~..

O.II'F

GND

Although the internal power dissipation is automatically limited, the maximum junction temperature of the device must
be kept below + 125°C in order to meet data sheet specifications. An adequate heatsink should be provided to assure
this limit is not exceeded under worst-case operating conditions (maximum input voltage and load current) if reliable
performance is to be obtained.

1
-L
TL/H/l04B4-9

. . Required if regulator input is more than 4 inches from input filter capacitor
(or if no input filter capacilor is used).

• 'Optional for improved transient response.

•
1-169

~National

~ semiconductor

LM342 Series
3·Terminal Positive Regulators
General Description
The LM342-XX series of three-terminal regulators is available with several fixed output voltages, making them useful
in a wide range of applications. One of these is local on card
regulation, eliminating the distribution problems associated
with single pOint regulation. The voltages available allow
these regulators to be' used in logic systems, instrumentation, HiFi, and other solid state electronic equipment. Although designed primarily as fixed voltage regulators these
devices can be used with external components to obtain
adjustable voltages and currents.
The LM342-XX series is available in the plastic TO-202
package. This package allows these regulators to deliver
over 0.25A if adequate heat sinking is provided. Current limiting is included to limit the peak output current to a safe
value. Safe area protection for the output transistor is provided to limit internal power dissipation. If internal power
diSSipation becomes too high for the heat sinking provided,
the thermal shutdown circuit takes over, preventing the IC
from overheating.
Considerable effort was expended to make the LM342-XX
series of regulators easy to use and minimize the number of
external components. It is not necessary to bypass the

output, although this does Improve transient response. Input
bypassing is needed only if the regulator is located far from
the filter capacitor of the power supply. '
For output voltage other than 5V, 12V and 15V the LM117
series provides an output voltage range from 1.2V to 57V.

Features
• Output current in excess of 0.25A
• Internal thermal overload protection
El No external components required
• Output transistor safe area protection
• Internal short circuit current limit
• Available in plastic TO-202 package
• Special circuitry allows start-up even if output is pulled
to negative voltage (± supplies)

Voltage Range
LM342-5.0
LM342-12
LM342-15

5V
12V
15V

Schematic Diagram

r--.....--.....-----------------1""'""--......----..... 1N
--ov

Rll
1.9

r-+-~--======:j'-~I--~VOUT

R3
576
R2
3.41k
Dl

D2

Rl
3.B9k

R5
7.Bk
R13
2.23k
Q6

R6
2.B4k

~~~-~--~--_4--~I_------~~--------------------------~-o~D
TUH/l0485-1

1-170

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Vo = 5V
Vo = 12V and 15V

Output Voltage

5V

12V

15V

Input Voltage (unless otherwise noted)

10V

19V

23V

Output Voltage
(NoteS)

Units

Min Typ Max Min Typ Min

Min

Typ

Max

TJ = 25'C

4.8

14.4

15

15.6

V

1 mA,;;; 10';;; 250 mAand

12,6 14,25
15.75
4.75
5.25 11.4
(7.5,;;;VIN';;;20) (14.8,;;;VIN,;;;27)
(18,;;;VIN';;;SO)

V

Parameter

Conditions

AVo

Line Regulation

TJ = 25'C, 10 = 250 mA

AVo

Load Regulation

TJ = 25'C, 1 mA,;;; 10';;; 250 mA

AVo

Long Term Stability

10

Quiescent Current

TJ = 25'C

Ala

Quiescent Current
Change

TJ = 25'C.1 mA,;;; 10';;; 250 mA

AVIN

TBD

O'C to + 70'C, 10 = 250 mA (Note 2) unless noted

VMIN ,;;; VIN ,;;; VMAX

Vn

SOO'C

O'Cto +70'C

Electrical Characteristics TA =

Vo

Lead Temperature (Soldering, 10 sec,)

Internally Limited

Operating Temperature Range

Symbol

-65'C to + 150'C

ESD Susceptibility

SOV
S5V

Internal Power Dissipation

125'C

Maximum Junction Temperature
Storage Temperature Range

5

5.2

55
(7,S,;;;VIN,;;;25)

11.5

f=120Hz

Input Voltage
Required to Maintain
Line Regulation

TJ = 25'C, 10 = 250 mA

Thermal Resistance
Junction to Case

P Package

Thermal Resistance
Junction to Ambient

P Package

100
(17,7,;;;VIN';;;SO)

120

50

150

48

60

mV
mV
mV/khrs

6

6

6

mA

0,5

0,5

0,5

mA

1,5
(7,3,;;;VIN,;;;25)

1,5
(14.6,;;;VIN,;;;30)

1,5
(17,7,;;;VIN';;;30)

mA

40

96

120

/LV

56

dB

Output Noise Voltage TJ = 25'C, f = 10 Hz-10 kHz
Ripple Rejection

12.5

100
(14.6,;;;VIN';;;SO)

20

TJ = 25'C, VMIN ,;;; VIN ,;;; VMAX

12

50

AVOUT

64

7,3

44

56

14,6

42

17.7

V

15

15

15

'C/W

80

80

80

'C/W

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions. SBe the Electrical Characteristics.
Note 2: The electrical characteristics data represent pulse test conditions with junction temperatures as shown at the initiation of tests.

Note 3: The temperature coefficient of VOUT Is typically within 0.Q1 % Vol'e,

1-171

III

CD

.~

en

Typical Performance Characteristics
Maximum Average Power
Dissipation (TO-202 Package)

Peak Output Current
0.7 r--1TJ=obc -

--!FINITE HEAT SINK

~
z

0

I
~

10.0

3:

0.6

5.0

~
a

0.5

5

0.3

0

0.2

~

3.0 WITH 150 C/W HEAT SINK -

1.0

~

0.5
0.3

===
o

ENO' HEAT SINK

0.4

5

~~

~

60

45

75

o

z

60

:t

"2
3

60

z

50

0

§

PART NO.
LM342-5.0
LM432-12
LM342-15

'"

40

o

15

20

10

25

10

100

lk

10k

5

5

10

lOOk

i'..

........

5

Vo=5V _
10=40rnA
TJ =25OC 10

15

20

25

Co=rPFj

100

lk

10k

lOOk

1M

VOUT =5V
Y,N = 10V
lOUT = 40 mA

"'-

2.64

2.56

ISO

Quiescent Current

2.68

I

125

/Co-lpF

0.0 1

2.9

2.50

100

0

a

!:l

75

FREQUENCY (Hz)

l-

\j

50

Y,N = 10V
Vo=5V
10=250rnAF
TJ =25OC

FREQUENCY (Hz)

Quiescent Current

!Z

25

O. 1

5

4V,N =7Vp.. p
10=250mA
TJ =250 C

2.76

~

o

~2!

V,N = llV

OUTPUT VOLTAGE (V)

!E

o

Output Impedance

Vo=5V

'"

~ ...::

JUNCTION TEMPERATURE (OC)

\j

20

_~OrnA-

0.5

i

30

s

30

~

Y,N
llV
19V
23V
10

5

I-

o
5

25

r--

~ 1.0
5

I'-...

20

4io =liomv

;!

40

ill
50

""

~

~

1

70

ill
~

1.5

=~50.J.

....:;.

Ripple Rejection

•

§

a

so

f=120Hz
4V,N =7Vp_ p
10=250mA
TJ =25OC

"2

15

2.0

INPUT-OUTPUT DIFFERENTIAL (V)

Ripple Rejection
70

10

'L

w

~

~

I
I

o
30

~

...... l"'o..

~ TJi'50iC.......

0.1

15

~VOUT=.!!l~

J-TJ= 2jOC

AMBIENT TEMPERATURE (OC)

3

Dropout Voltage
~ 2.5

O.B

30.0

30

1

-

1.9

35

o

INPUT VOLTAGE (V)

25

50

75

100

125

ISO

JUNCTION TEMPERATURE (OC)
TL/H/l0485-3

1-172

Connection Diagram

Typical Applications

TO-202 (P) Plastic Package

Fixed Output Regulator

o

INPUT

o--1~-I:

Lt.f342-XX

:..-.....- - 0 OUTPUT

GND
4-

GND

:,:: C2"

.,
TL/H/l0485-4
'Required if the regulator is located far from power supply filter
"Although not required, C2 does improve transient response. (If needed, use 0.1 I'F ceramic disc.)

Adjustable Output Regulator
... OUTPUT

INPUT -

INPUT

o--1~-I:

Lt.f342-5.0

J..-.....-o

I

OUTPUT

Rl

. . . . . : R2

'-GND

~----------------~l---'GND

TLlH/l0485-2

Order Number LM342P-5.0,
LM342P-12 or LM342P-15
See NS Package Number P03A

-==

TL/H110485-5
Vo

= 5V + (5V/RI + 10) R2

5V1Rl

> 310, Load Regulation (LR)

=

[(Rl

+

R2)/R1J x (Lr of LM342·05)

Current Regulator
INPUT 0 - -.....--11

Lt.f342-XX

I-

1
......_ _,...-_---'

Rl

~----...-_oOUTPUT

TL/H/l0485-6
lOUT = V2-3/Rl

+

10

Ala';; 1.5 rnA over line and load changes

1-173

•

Typical Applications

(Continued)
High Output Voltage Regulator
1-....-

LM342-15

03"
lN4001

R
470

5W

Cl·
0.22J1oF

....0 VOUT =39V @ 250mA

C2
0.1 JIoF

Zl
lN5359
24V

TL/H/l0485-7

'Necessary if regulator is located far from the power supply filter
"03 aids in full load start-up and protects the regulator during short circuits from high input to output voltage differentials

± l5V, 250 mA Dual Power Supply
LM342-15

1-....- - - 0

VOUT = 15V @ 250 mA

GNOo---~----~~----~-~-oGNO

-VIN = -20V 0 - - -....-1

LM320MP-15

1 - - 0 - - - 0 -VOUT =-15V@ 250mA
TL/H/l0465-6

Variable Output Regulator O.5V-18V

LM342-5.0

VIN =20V

R2

Cl
o.22 J1oF

I

-

e3·
I1J1oF

-

110
R3
Rl

6

-VIN =-10V

VOUT

= VG +

Your =

SV. Rl

=

(-VIN/lo LM342)

SV(R2/R4) for (R2

+

R3)

= (R4 + RS)
= 0.1. (R3/R4) = 0.9

30pF

A O.SV output will correspond to (R2/R4)

TL/H/l046S-9

'Solid tantalum

1-174

~National

~ Semiconductor

LM431A
Adjustable Precision Zener Shunt Regulator
General Description

Features

The LM431A is a 3-terminal adjustable shunt regulator with
guaranteed temperature stability over the entire temperature range of operation. The output voltage may be set at
any level greater than 2.5V (VREF) up to 36V merely by
selecting two external resistors that act as a voltage divided
network. Due to the sharp turn-on characteristics this device
is an excellent replacement for many zener diode applications.

• Average temperature coefficient 50 ppml"C
• Temperature compensated for operation over the full
temperature range
• Programmable output voltage
• Fast turn-on response
• Low output noise

Connection Diagrams

I

REF

CATHODE- 1

3

2
II

8 -REFERENCE

7 -ANODE

ANODE- 2
II

I

Y--- ·T- h~

ANODE- 3

6 -ANODE

5 -NC

NC- 4

CATHODE

TLlH/l0055-2

ANODE
TLlH/l0055-1

Top View

Top View
Order Number LM431ACM
See NS Package Number M08A

Order Number LM431ACZ or LM431AIZ
See NS Package Number Z03A

1-175

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Storage Temperature Range
- 65·C to + 150·C
Operating Temperature Range
Industrial (LM431AI)
- 40·C to + B5·C
O·Cto +70"C
Commercial (LM431AC)
Lead Temperature
TO-92 Package/SO-B Package
(Soldering, 10 sec.)
265·C
Internal Power Dissipation (Notes 1, 2)
TO-92 Package
0.7BW
SO-B Package
0.B1W

LM431A
Electrical Characteristics TA =

Cathode Voltage
37V
Continuous Cathode Current
-10mAto +150mA
-0.5V
Reference Voltage
10mA
Reference Input Current
Operating Conditions
Min
Max
Cathode Voltage
37V
VREF
Cathode Current
1.0mA
100mA
Note 1: TJ Max = ISO'C.
Note 2: Ratings appy to ambient temperature at 25"C. Above this temperature, derate the T0-92 at 6.2 mWI'C, and the SO·8 at 6.5 mWI'C.

25·C unless otherwise specified
Min

Typ

Max

Units

2.440

2.495

2.550

V

B.O

17

mV

-1.4

-2.7

-1.0

-2.0

RI = 10kO, R2 = 00,
II = 10 mA (Figure 2)

2.0

4.0

p.A

Deviation of Reference
Input Current over
Temperature

RI = 10kO,R2 = 00,
11=10mA,
TA = Full Range (Figure 2)

0.4

1.2

p.A

IZ(MIN)

Minimum Cathode Current
for Regulation

Vz = VREF (Figure 1)

0.4

1.0

mA

IZ(OFF)

Off-State Current

Vz = 36V, VREF = OV (Figure 3)

0.3

1.0

p.A

Symbol

Parameter

Conditions

VREF

Reference Voltage

Vz = VREF, II = 10 mA (Figure 1)

VOEV

Deviation of Reference
Input Voltage Over
Temperature (Note 3)

Vz = VREF, II = 10 mA,
TA = Full Range (Figure 1)

Ratio of the Change in
Reference Voltage to the
Change in Cathode
Voltage

Iz = 10mA
(Figure 2)

IREF

Reference Input Current

""IREF

aVREF
aVz

Vz from VREF to 10V

mVIV
Vz from 10V to 36V

Dynamic Output
Vz = VREF,
0.75
Impedance (Note 4)
Frequency = 0 Hz (Figure 1)
Note 3: Deviation of reference Input voltage, VOEV, Is defined as the maxlThe average temperature coefficient of the reference Input voltage, '" VREF,
mum variation of the reference Input voltage over the full tamperature range.
Is defined as:

rZ

°

coVREFEE!!! =

±[ VREF
VMax-VMln]
±[ VOEV ]
(at2S'C) 108 = VREF (at 25"C) 108

~

VMAX

VYIN

7

I

Vor:v

=VWAX -

VMIN

I
I
I
I
I

TEMPERATURE

~-~

[ 8.0mV ]
"VREF

~

2496""mv
70'C

108

= +46ppm/'C

Note 4: The dynamic output Impedance, rz, Is defined as:
rz = AVz
Alz
When the device Is programmed with two external reslstora, RI and R2, (see
FIgure 2), the dynamic output Impedance of the overall clrcul~ rz, Is defined
as:

I

Tl

~-~

Where:
T2 - T1 = full temperature change.
co VREF can be positive or negative depending on whether the slope Is posl.
tlve or negative.
Example: VOEV ~ 8.0 mY, VREF = 2495 mY, T2 - Tl = 70'C, slope Is
positive.

T2
TL/H110055-7

AVz [ rzl+AI]
rz=-III
Alz
A2

1-176

~------------------------------------------------------------------------------------,

,j::o,
Co)

....
»

r----------------.....- ......- .....---.--- CATHODE
(VZ)

R3
2.5 kD.

R5
640D.

Rl
3.3.a.

~_______~------~-----~_--~--ANODE

(GND)
TLlH110055-3

DC Test Circuits

--"1"""'-.-11 -

IN

r-

3:

Equivalent Circuit

--'lJ"""'-.-11 -

Vz

IN

Vz

Rl

~ IZ
R2

TLIH110055-4

TLlH110055-5

FIGURE 1. Test Circuit for Vz = VREF

Note:Vz

IN--:I

= VREF(1 +

+ IREF"R1
FIGURE 2. Test Circuit for Vz > VREF
R11R2)

VZ

yh'"
TLIH110055-6

FIGURE 3. Test Circuit for Off-State Current

1-177

Typical Performance Characteristics
Input Current vs Vz

~ 1000

=25"C
Vz =VREF

Thermal Information

150

Vz = vREF f--+----1f--t--f

1

i"o..

l/

I

~ ........

jlzMIN

o
o

Input Current vs Vz
TA .. 25"C

TA

I
~

V

1.0

2.0

70

85

50

1.0

125

TEMPERATURE - "C

CAlIIOD[ VOLTAGE - V

100 f--+--t--t--+--t--l

2.0

CAlIIOD[ VOLTAGE - V
TL/H/l0055-8

Dynamic Impedance vs
Frequency
15
TA

= 25"C

Vz = VREF

C\

I

I

I:l 10

;

~ s.o
~

/

o

1.0k

10k

f""\.

1.0k.o.

I
/

lOOk

50.0.

l'z=10mA
l.oM

ION

FREQUENCY - Hz

TUH/l0055-10

TL/H/l0055-9

Note 1: The areas under the curves represent conditions that may cause the
device to oscillate. For curves B. C, and 0, R2 and V + were adjusted to
establish the Initial Vz and Iz conditions with CL = O. V+ and CL were then
adjusted to determine the ranges of stability.

Stability Boundary Conditions

J

100

..

E

...
'"'"
=>
...cu
I-

Z

0

:t:

5

=VREF
=5 V AT Iz =10 rnA
=10V AT Iz = lOrnA
=15VAT Iz = lOrnA

A Vz
B Vz

90

80 C Vz
70 o Vz
80

(NOTE 1)
STABLE

i

A

50

B

1\

STABLE

40
30
20

TA

10

o

10pF

/I I
II I

=25 C
0

",C

L

l\

0

'//L ~~
l00pF

l000pF

O.Q1pF

O.lpF

1\
10pF

LOAD CAPACITANCE
TL/H/l0055-11

Test Circuit for Curve A Above

Test Circuit for Curves B. C and D Above
Rl ...
10k.o.

+
CL

VREF

l'K

150.0.

+

V+

R2

TLlH/l0055-12

TL/H/l0055-13

1·178

r-

s::

Typical Applications

.Qo,

Shunt Regulator
V+

I
I
I
I

V+

Vo

..l...

VREF

4""

OUT

VON"" 2V
VOff V+

=

IN
VTH "" 2.5V

TL/H/l0055-14
Vo '" (1

+~)

GND

VREF

TLlH/l0055-15

Series Regulator
V+

Output Control of a Three
Terminal Fixed Regulator
301).

V+

Vo

0.01
J.lF
Rl
Vo
R2
R2
TL/H/l0055-16
Vo'" (1

....

w

Single Supply Comparator with
Temperature Compensated Threshold

+~) VREF
Vo = (1

+~) VREF

Vo MIN = VREF

1·179

+

5V

TLlH/l0055-17

»

Typical Applications (Continued)
Higher Current Shunt Regulator

CrowBar

v+--~~-,----~~------~---Vo

v+

~-.-----.------~---~
Rl

Rl

R2

R2
TLlH/10055-18

Vo = (1

TL/H/10055-19

+ i*)VREF

VLlMIT:::: ( 1

+ i*)VREF

Over Voltage/Under Voltage
Protection Circuit
V+--~~----------~~----.-------~

Rl0

R1A

R20

R2A

TL/H/10055-20

LOW LIMIT:::: VREF ( 1

+ R1B)
R2B + VBE

HIGH LIMIT:::: VREF (1

+ :~)

Voltage Monitor
V+--~-----------1~~~~--~

R1A

Rl0

R2A

R20

TLlH/10055-21

R1B)
LOW LIMIT:::: VREF ( 1 + R2B

LED ON WHEN
LOW LIMIT < V+ < HIGH LIMIT

R1A)
HIGH LIMIT:::: VREF ( 1 + R2A

1-180

r-----------------------------------------------------------------------------~

Typical Applications

(Continued)

~

....
)0

Co)

Current Limiter or Current Source

Delay Timer
v+--------~--~~~~__,

v+--.....---+"""
R

OFF

r
ii:

c
TUH/10055-23

10

= VREF
RCL

TL/H/10055-22

V+
DELAY = R· C· In (V+) _ VREF

Constant Current Sink

v+

TL/H/10055-24

1·181

~National

~ semiconductor

LM723/LM723C Voltage Regulator
General Description

Features

The LM723/LM723C is a voltage regulator designed primarily for series regulator applications. By itself, it will supply
output currents up to 150 mA; but external transistors can
be added to provide any desired load current. The circuit
features extremely low standby current drain, and provision
is made for either linear or foldback current limiting.
The LM723/LM723C is also useful in a wide range of other
applications such as a shunt regulator, a current regulator or
a temperature controller.
The LM723C is identical to the LM723 except that the
LM723C has its performance guaranteed over a O"C to
+ 70"C temperature range, instead of - 55°C to + 125D C.

• 150 rnA output current without external pass transistor
• Output currents in excess of 10A possible by adding
external transistors
• Input voltage 40V max
• Output voltage adjustable from 2V to 37V
• Can be used as either a linear or a switching regulator

Connection Diagrams
Dual-In-Llne Package

Metal Can Package
CURRENT

Ne

14

CURRENT SENSE

3

12

NC
FREQUENCY
COMPENSATION
y+

INVERTING INPUT
NON-INYERTING
INPUT
YREF

4

11

Yc

5

10

YOUT

Y-

7

CURRENT LIt-lIT

2

13

LIMIT

INVERTING
INPUT
NON·INVERTING
INPUT

Yz

9

NC
TLlH/8563-3

TL/H/8563-2

Top View

Note: Pin 5 connected to case.

Order Number LM723J, LM723J/883, LM723CJ,
LM723CM or LM723CN
See NS Package J14A, M14A or N14A

Order Number LM723H or LM723CH
See NS Package H10C

Top View

Equivalent Circuit*
V'

FREOUENCY
COMPENSATION
9

CURRENT

FREQ COMP

LIMIT

Vo

CURRENT
SENSE

• ..
3

2 It. 20 19

18

I.

-IN

v+

17

.

ve

15

TEMPERATURE
COMPENSATED
ZENER

+IN

8

9 10 11 12 13

VREr
v-

OUT

Vz

TL/H/8563-20

VO..

Top View

i

v-

1
CURRENT
SENSE

Yz

TLlH/8563-4

'Pin numbers refer to metal can package.

1-182

Order Number LM723E/883
See NS Package E20A

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 9)
Pulse Voltage from V+ to V- (50 ms)

50V

Continuous Voltage from V+ to V-

40V

Input-Output Voltage Differential

40V

Maximum Amplifier Input Voltage (Either Input)

Internal Power Dissipation Metal Can (Note 1)
Cavity DIP (Note 1)
Molded DIP (Note 1)

- 55'C to + 150'C
Operating Temperature Range LM723
LM723C
O'Cto +70'C
Storage Temperature Range Metal Can -65'C to + 150'C
Molded DIP - 55'C to + 150'C
Lead Temperature (Soldering, 4 sec. max.)
Hermetic Package
Plastic Package

8.5V

Maximum Amplifier Input Voltage (Differential)

5V

Current from Vz

25mA

Current from VREF

15mA

800mW
900mW
660mW

300'C
260'C

ESD Tolerance
1200V
(Human body model, 1.5 kO in series with 100 pF)

Electrical Characteristics (Notes 2, 9)
LM723C

LM723
Parameter

Conditions

Min Typ

Max Min Typ

Max

VIN = 12Vto VIN = 15V
-55'C S; TA S; +125'C
O'C S; TA S; +70'C
VIN = 12V to VIN = 40V

0.01

0.1
0.3

0.01

0.1

0.02

0.2

0.1

0.3
0.5

Load Regulation

IL = 1 mA to IL = 50 mA
-55'C S; TA S; +125'C
O'C S; TA S; +70'C

0.03

0.15
0.6

0.03

0.2

Ripple Rejection

f
f

Average Temperature Coefficient of Output Voltage (Note 8)

-55'C S; TA S; +125'C
O'C S; TA S; +70'C

Short Circuit Current Limit

Rsc = 100, VOUT

Line Regulation

=
=

0.6
74
86

50 Hz to 10 kHz, CREF = 0
50 Hz to 10kHz, CREF = 5 ,..F

=

65
6.95 7.15

BW = 100 Hzto 10 kHz, CREF = 0
BW = 100 Hz to 10 kHz, CREF = 5,..F

65
7.35 6.80 7.15

86
2.5

Long Term Stability
Standby Current Drain

=

0, VIN

=

1.7

30V

1.7

V
,..Vrms
,..Vrms

0.05
3.5

%/'C
mA

7.50

86
2.5

0.05
IL

%VOUT
%VOUT
%VOUT

%rC
0.003 0.015

0

%VOUT
%VOUT
%VOUT
%VOUT

dB
dB

0.002 0.Q15

Reference Voltage
Output Noise Voltage

74
86

Units

%/1000 hrs
4.0

mA

Input Voltage Range

9.5

40

9.5

40

V

Output Voltage Range

2.0

37

2.0

37

V

Input-Output Voltage Differential

3.0

38

3.0

38

V

IJJA

Molded DIP

105

105

'C/W

IJJA

Cavity DIP

150

150

'C/W

IJJA

H10C Board Mount in Still Air

165

165

'C/W

IJJA

H10C Board Mount in 400 LF/Min Air Flow

66

66

'C/W

IJJA

SO
22

IJJC

125

'C/W

22

'C/W

Note 1: See derating curves for maximum power rating above 25°C.

Note 2: Unless otherwise specified, TA
impedance as seen by error amplifier

s:

~

2S'C, VIN

~

V+

~

Ve

~

12V, V-

~

0, Your

~

SV, IL

~

1 mA, Rse

~

0, C1 ~ 100 pF, CREF

~

a and divider

10 kO connected as shown in Figure 1. Una and load regulation specifications are given for the condition of constant chip

temperature. Temperature drifts must be taken into account separately for high dissipation conditions.

Note 3: L1 is 40 turns of No. 20 enameled copper wire wound on Ferroxcube P36/22·387 pot core or equivalent with 0.009 in. air gap.
Note 4: Figures in parentheses may be used if R1/R2 divider Is placed on opposite input of error amp.
Note 5: Replace R1/R2 in figures with divider shown in Figure 13.

Note 6: V+ and Vee must be connected to a + 3V or greater supply.
Note 7: For metal can applications where Vz is required, an external 6.2V zener diode should be connected in series with VOUT'

Note 8: Guaranteed by correlation to other tests.
Note 9: A military RETS specification is available on request. At the time of printing. the LM723 RETS specification complied with the Min and Max limits in this
table. The LM723E, H, and J may also be procured as a Standard Military Drawing.

1-183

Typical Performance Characteristics
Load RegulatIon
CharacterIstIcs wIth
Current LImItIng

Load RegulatIon
Characterlstica wIth
Current LImItIng

0.05

0.1

J

~~C

.. -0.0&
I

15

-0.1

S

-us

Ii

=

..J
5.

""""""':1"-

TAaZ C

I

TAa 121'C ~

VOUT a ~IJ.

.0.2

v:. ~ .12V

II!

f-

o

10 11 10 II
OUTPUT CURRENT ImAI

~

:::

..~
..II:
>

!;

~

~

...:e~
~

-rTA a I2I'C

r-- TA _12&Oe

u -rTA a_II'C

~

;-

i

0.1

0.1

20
40
10
10
OUTPUT CURRENT (mAl

0.1

-4.0

I"'- ..!!.U':UT VOLTAGE-

4.0

II

iii
2.0 ;!
c

B.O

.. !Ii..
.. ...1l:
. ~.
..
i
.. ".0
".0
-4.0

35

120

10 ~

"

.
!!i

40

IL -1mAtol .. -lDmA

11

100

~

~

T lal~I,J-

OA

YOU,-VA.'
'LaO
10

41

4.0

·It

OUTPUT VOLTAGE"

15

V1N -+12V

Vou ,-+5V ·20
',a40mA
TA a II'C
·30
Roc-O

TIME I_sl

21

31

40

10

..S i..
.. I..
i ..~

c,a~

YOUT -+IV
VIN -+lIV

10

\

30

Output Impedence V8
Frequency

:; S

-I

20

INPUT VOLTAGE IVI

I!;

S~

41

~al'J-

110

LOAD CURRENT

!; -4.0

31

(VI

TlaJI,J-

10

, - ......

21

Z.D
1.8
1.8
lA
1.2
1.0
0.1
0.1
0.2

I

~ >

21

..3 :1
Ii i
..." ..:;.'"
c:

tiD

-r-. ...

10

~

Stendby Current DraIn V8
Input Voltage
100

1

0.3

-2.0 ~

I'"

11

·1

'""1"-01..

1

VIN - YOUT

~

'-ffifURRENT
Roc a 1011

1Il

IL -lmA
T.aZI'C
RocaO

I!:

100

'I..

0.1

.10

!:j

>
!; -1.0

10

Load Transient Response

2.0

I

10

-=-~

YOUT. +&V

-0.1 Roc a 0
TA _21i°C
.0.2
-I

JUNCTION TEMPERATURE I'CI

'NPUTVOLTAGE

V1N -+12
VOUT - +5V

'"

1

40

.....

100

I

4.0

20

IL -1 mA

LINE

:.l

"- I" SENSE VOLTAGE

0.7

Q.4

'"
B

S

o

C

\I

Rrll"

-r1Aarl'~ -

o

1'\ 1\Ti a ill'I

1

I. I-LlFr~ , .....

0.1

o

\ '\

T.a2I'C~

1

-0.3

Line Transient Response

.
~
....~
..
...

~

6Y-+3V

0.1

Current LImiting
CharacterIstics vs
JunctIon Temperature

:OU!;:~.~~1~

0.1

I

vou,-+&V
RocaO
TA· +25·C

0.1

OUTPUT CURRENT ImAI

1.0

1.0

.!!

I"\'

·0.1

Current LImItIng
Characterl8tlca
1.2

..J
..
5.

II!I!
·0.1

·u

30

0.3

VOUT· IV, VIN • +12V
Roc a l0U "'" -

RIC-'OU

-0.11

Load & LIne Regulatlon vs
Input-output Voltage
DifferentIal

RIC-.

III

T.a2I'C
... -lImA

1.0

c" a l.F

~

'"

0.1

.01

41

I.

100

lOOk

1M

FREQUENCY (Hz)

TIME ""I

TL/H/8563-6

Maximum Power Ratings
Noise va Filter CapaCitor
(CREF In Circuit 01 Figure t)
(Bandwidth 100 Hz to 10 kHz)

LM723
Power Dlaslpatlon vs
Ambient Temperature

1000
900

100
50 .......

BOO

i'.

DIP
Hl0e

70D

20

o
o

",

.01

.1

CmC!~.~K

R2

INV.

R5
In

.L

I

v-

o

~3234

CS - - - ,

,-~

"

CDMP

-,ToICI
500 pF
REGULATED
OUTPUT

...H...

Tl/H/8563-14

TypIcal Performance
Regulated Output Voltage
Une Regulation caV'N ~ 20V)
Load Regulation call = 50 mAl

+ 50V
15mV
20 mV

FIGURE 7. Positive Floating Regulator

V,"
R610K

Vee

V.I-----...- - I
R3
3K

R2

LM123
LM723C

•

CL

cs

....- .......+--+--IN.1.
R4
3K

RI

CI
100 pF

v-

+ __...___.._________+ ___...._

L...._....

~~~~~~TED

TL/H/8563-15

Typical Performance
Regulated Output Voltage
Line Regulation (a VIN = 20V)
Load Regulation (all = 100 mAl

-IOOV
30 mV
20 mV

FIGURE 8. Negative Floating Regulator

1-187

Typical Applications

(Continued)

R5
3K

V'

Vee

r------t VREF
D1

IN2071
RI

LM723
LM723C

csl--e_---'
INV.

CaMP

TL/H/B563-1B

Typical Performance
Regulated Output Vollage
Line Regulation (4.0A2N6124

OUT ......-

...........-I

........-+-.........-+VO
32V....""""'''''''''-............
I ",,220 mA-

O.II'F

L...--+-+VO

O.331'F

TLlHll0054-14

TLlHl10054-17

Note 1: External series pass device is not short circuit protected.
Note 2: If load is not ground referenced, connect reverse biased diodes from
outputs to ground.

1-196

r-------------------------------------------------------------------------, r
i:
.....
~National
~
Q)

~ Semiconductor

><

LM78LXX Series 3-Terminal Positive Regulators
General Description

Features

The LM78LXX series of three terminal positive regulators is
available with several fixed output voltages making them
useful in a wide range of applications. When used as a zener diode/resistor combination replacement, the LM78LXX
usually results in an effective output impedance Improvement of two orders of magnitude, and lower quiescent current. These regulators can provide local on card regulation,
eliminating the distribution problems associated with single
point regulation. The voltages available allow the LM78LXX
to be used in logic systems, instrumentation, HiFi, and other
solid state electronic equipment.
The LM78LXX is available in the metal three-lead TO-S9(H)
package, the plastic TO-92 (Z) package, and the plastic
50-8 (M) package. With adequate heat sinking the regulator
can deliver 100 mA output current. Current limiting Is Included to limit the peak output current to a safe value. Safe area
protection for the output transistors is provided to limit internal power dissipation. If Internal power dissipation becomes
too high for the heat sinking provided, the thermal shutdown
circuit takes over preventing the IC from overheating.

• Output voltage tolerances of ± 5% (LM78LXXAC) over
the temperature range
• Output current of 100 mA
• Internal thermal overload protection
• Output transistor safe area protection
• Internal short circuit current limit
• Available in plastic TO-92 and metal TO-S9 and plastic
50-8 low profile packages
• No external components
• Output voltages of 5.0V, S.2V, 8.2V, 9.0V, 12V, 15V

Connection Diagrams
(TO-39)
Metal Can Package (H)

SO-S Plastic (M)
(Narrow Body)

(T0·92)
Plastic Package (Z)

OUTPUT
INPUT

(?

GNO

leASEI

1· ......" 8 i-V1N

VOUT GND- 2

7 i-GND

GND- 3

6 i-GND

NC- 4

5

~NC

"'BGNO

A.

V'

TL/H17744-3

-

TL/H/7744-1

TL/H17744-2

Bottom View

Top View

Order Number LM7SL05ACH,
LM7SL 12ACH or LM7SL 15ACH
See NS Package Number H03A

Order Number LM7SL05ACM,
LM7SL 12ACM or LM7SL 15ACM
See NS Package Number MOSA

1-197

Bottom View
Order Number
LM7SL05ACZ, LM7SL09ACZ,
LM7SL 12ACZ, LM7SL 15ACZ,
LM7SL62ACZ or LM7SLS2ACZ
See NS Package Number Z03A

•

Absolute Maximum Ratings

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Power Dissipation (Note 5)
Input Voltage

Storage Temperature
-65'Cto
Operating Junction Temperature
O'C to
Lead Temperature (Soldering, 10 seconds)
ESD Susceptibility (Note 2)

Internally Limited

+ 150'C
+ 125'C
265'C
2kV

35V

LM78LXXAC Electrical Characteristics

Limits in standard typeface are for TJ = 25'C, bold typeface applies over the O'C to + 125'C temperature range. Limits are
guaranteed by production testing or correlation techniques using standard Statistical Quality Control (SQC) methods. Unless
otherwise specified: 10 = 40 mA, CI = 0.33 p.F, Co = 0.1 p.F.

LM78L05AC
Symbol
Vo

Unless otherwise specified, VIN = 10V
Parameter

Conditions

Output Voltage

Min

Typ

Max

4.B

5

5.2

7V,,;; VIN";; 20V
1 mA ,,;; 10 ,,;; 40 mA
(Note 3)

4.75

5.25

1mA,,;;lo,,;;70mA
(Note 3)

4.75

5.25

I!>.Vo

Line Regulation

7V,,;; VIN";; 20V

1B

75

I!>.Vo

Load Regulation

BV,,;; VIN";; 20V

10

54

1 mA,,;; 10";; 100 mA

20

60

10

Quiescent Current

5

30

I!>.lo

Quiescent Current Change

BV,,;; VIN";; 20V

1.0

1 mA ,,;; 10 ,,;; 40 mA

0.1

Vn

Output Noise Voltage

f = 10Hzto 100kHz
(Note 4)

I!>.VIN
I!>.VOUT

Ripple Rejection

f = 120Hz
BV,,;; VIN";; 16V

1mA,,;;lo";;40mA

IpK

Peak Output Current

I!>.Vo
I!>.T

Average Output Voltage Tempco

VIN
(Min)

Minimum Value of Input Voltage
Required to Maintain Line Regulation

3

10 = 5mA

47

V

mV

5
mA

40

p.V

62

dB

140

mA

-0.65

mV/,C

6.7

1-19B

Units

7

V

LM78LXXAC Electrical Characteristics

Limits in standard typelace are lor TJ = 25°C, bold typeface applies over the O"C to + 125°C temperature range. Limits are
guaranteed by production testing or correlation techniques using standard Statistical Quality Control (SQC) methods. Unless
otherwise specilied: 10 = 40 rnA, CI = 0.33 ,...F, Co = 0.1 ,...F. (Continued)

LM78L62AC Unless otherwise specilied, VIN =
Symbol
Vo

Parameter

12V
Conditions

Output Voltage

Min

Typ

Max

5.95

6.2

6.45

S.5V ,;; VIN ,;; 20V
1 rnA ,;; '0 ,;; 40 mA
(Note 3)

5.9

6.5

1mA,;;lo,;;70mA
(Note 3)

5.9

6.5

S.5V ,;; VIN ,;; 20V

65

175

9V,;; VIN';; 20V

55

125

1 mA,;; '0';; 100 rnA

13

SO

1 mA,;;'0,;;40mA

6

40

2

5.5

aVo

Line Regulation

aVo

Load Regulation

10

Quiescent Current

ala

Quiescent Current Change

SV,;; VIN';; 20V

1.5

1 rnA,;; '0';; 40 rnA

0.1

Vn

Output Noise Voltage

1= 10 Hz to 100kHz
(Note 4)

aVIN
aVOUT

Ripple Rejection

I = 120Hz
10V ,;; VIN ,;; 20V

IpK

Peak Output Current

aVo
aT

Average Output Voltage Tempco

VIN
(Min)

Minimum Value 01 Input Voltage
Required to Maintain Line Regulation

10 = 5mA

40

Units

V

mV

rnA

50

,...V

46

dB

140

rnA

-0.75

mVloC

7.9

V

II

1-199

LM78LXXAC Electrical Characteristics

Limits in standard typeface are forTJ = 25°C, bold typeface applies over the O"C to + 125°C temperature range. Limits are
guaranteed by production testing or correlation techniques using standard Statistical Quality Control (SQC) methods. Unless
otherwise specified: 10 = 40 mA, CI = 0.33,...F, Co = 0.1 ,...F. (Continued)

LM78L82AC Unless otherwise specified, VIN =
Symbol
Vo

AVO

14V

Parameter

Conditions

Output Voltage

Line Regulation

1 mAS: 10 S:70mA
(Note 3)

7.B

B.8

s: VIN s: 23V
12V s: VIN s: 23V
1 mA s: 10 s: 100 mA
1 mAS: 10 s: 40mA
11V

Quiescent Current

Ala

Quiescent Current Change

12V

Vn

Output Noise Voltage

f= 10Hzto100kHz
(Note 4)

AVIN
AVOUT

Ripple Rejection

f=120Hz
12V s: VIN s: 22V

VIN
(Min)

Minimum Value of Input Voltage
Required to Maintain Line Regulation

BO

175

70

125

15

BO

B

40

2

5.5

s: VIN s: 23V

1 mA

Peak Output Current

B.53

B.8

10

Average Output Voltage Tempco

Max

B.2

7.B

Load Regulation

AVO
AT

Typ

1tV s: VIN s: 23V
1mAS:10S:40mA
(Note 3)

AVO

IpK

Min
7.B7

1.5

s: '0 s: 40 mA

10 = 5mA

1-200

Units

V

mV

mA

0.1

39

60

,...V

45

dB

140

mA

-O.B

mVioC

9.9

V

LM78LXXAC Electrical Characteristics

Limits in standard typeface are for T J = 25'C, bold typeface applies over the Q'C to + 125'C temperature range. Limits are
guaranteed by production testing or correlation techniques using standard Statistical Quality Control (SQC) methods. Unless
otherwise specified: 10 = 40 mA, CI = 0.33 ",F, Co = 0.1 ",F. (Continued)

LM78L09AC Unless otherwise specified, VIN
Symbol
Vo

I:No

Parameter

Line Regulation

aVo

10

Quiescent Current

ala

Quiescent Current Change

aVIN

Conditions

Output Voltage

Load Regulation

Vn

= 15V
Min

Typ

Max

8.64

9.0

9.36

11.5V :0: VIN :0: 24V
1 mA :0: 10 :0: 40 mA
(Note 3)

8.55

9.45

1 mA :0: 10 :0: 70 mA
(Note 3)

8.55

9.45

11.5V:o: VIN :0: 24V

100

200

13V :0: VIN :0: 24V

90

150

1 mA:O: 10:0: 100 mA

20

90

1 mA :0: 10 :0: 40 mA

10

45

2

5.5

11.5V :0: VIN :0: 24V

1.5

1 mA :0: 10 :0: 40 mA

0.1

Output Noise Voltage
Ripple Rejection

aVOUT
IpK

Peak Output Current

aVo
aT

Average Output Voltage Tempco

VIN
(Min)

Minimum Value of Input Voltage
Required to Maintain Line Regulation

f = 120Hz
15V:O: VIN :0: 25V

10=5mA

38

Units

V

mV

mA

70

",V

44

dB

140

mA

-0.9

mVI'C

10.7

V

•
1-201

LM78LXXAC Electrical Characteristics

Limits in standard typeface are for TJ = 25"C, bold typeface applies over the O"C to + 125"C temperature range. Limits are
guaranteed by production testing or correlation techniques using standard Statistical Quality Control (SQC) methods. Unless
otherwise specified: 10 = 40 mA, Cr = 0.33 ,...F, Co = 0.1 ,...F. (Continued)

LM78L 12AC Unless otherwise specified, VrN =
Symbol
Vo

t:.Vo

Parameter

19V
Conditions

Output Voltage

Line Regulation

t:.Vo

Load Regulation

10

Quiescent Current

t:.IO

Quiescent Current Change

Vn

Output Noise Voltage

Min

Typ

Max

11.5

12

12.5

14.5V S; VrN S; 27V
1 mA S; 10 S; 40mA
(Note 3)

11.4

12.6

1 mA S; 10 S; 70 mA
(Note 3)

11.4

12.6

14.5V S; VrN S; 27V

30

16V S; VrN S; 27V

20

110

1 mA S; 10 S; 100mA

30

100

1mAS;loS;40mA

10

50

3

5

Ripple Rejection

t:.VOUT
IpK

Peak Output Current

t:.Vo
t:.T

Average Output Voltage Tempco

VrN
(Min)

Minimum Value of Input Voltage
Required to Maintain Line Regulation

f=120Hz
15V S; VrN S; 25V

10 = 5mA

mA

40

80

,...V

54

dB

140

mA

-1.0

mVI"C

13.7

1·202

mV

0.1

1mAS;loS;40mA

t:.VrN

V

180

1

16V S; VrN S; 27V

Units

14.5

V

LM78LXXAC Electrical Characteristics

Limits in standard typeface are for TJ = 25'C, bold typeface applies over the Q'C to + 125'C temperature range. Limits are
guaranteed by production testing or correlation techniques using standard Statistical Quality Control (SQC) methods. Unless
otherwise specified: 10 = 40 rnA, CI = 0.33 ,...F, Co = 0.1 ,...F. (Continued)

LM78L 15AC Unless otherwise specified, VIN =
Symbol
Vo

/lVo

/lVo

23V

Parameter

Conditions

Output Voltage

Line Regulation

Load Regulation

10

Quiescent Current

/llo

Quiescent Current Change

Min

Typ

Max

14.4

15.0

15.6

17.5V s: VIN s: 30V
1 rnA s: 10 s: 40 rnA
(Note 3)

14.25

15.75

1 rnA s: 10
(Note 3)

14.25

15.75

s: 70 rnA

s: VIN s: 30V
s: VIN s: 30V
1 rnA s: 10 s: 100 rnA
1 mAS: 10 s: 40 rnA
17.5V

37

250

20V

25

140

35

150

12

75

3

5

20V

s: VIN s: 30V

1

/lVIN

Output Noise Voltage
Ripple Rejection

/lVOUT
IpK

Peak Output Current

/lVo
/IT

Average Output Voltage Tempco

VIN
(Min)

Minimum Value of Input Voltage
Required to Maintain Line Regulation

f=120Hz
18.5V s: VIN

s:

28.5V

10 = 5mA

V

mV

rnA

0.1

1 mAS: lOS: 40 rnA
Vn

Units

37

90

,...V

51

dB

140

rnA

-1.3

mVl'C

16.7

17.5

V

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Electrical specifications do not apply when operating the device
outside of its stated operating conditions.
Note 2: Human body model, 1.5 kll in series with 100 pF.
Note 3: Power dissipation';; 0.75W.
Note 4: Recommended minimum load capacitance of o.ot I'F to limit high frequency noise.
Note 5: Typical thermal resistance values for the packages Bre:
H Package: Rth(J·C) = 26 'C/W, Rth(J·A) = 120 'C/W
Z Package: Rth(J.C) = 60 'C/W, Rth(J·A) = 230 'C/W
M Package: Rth(J.A) = 180 'C/W

1·203

II

Typical Performance Characteristics

10

."

Maximum Average Power
Dissipation (Z Package)
10

5.0

g

!

I
I<

;

Maximum Average Power
Dissipation (H Package)

:~:; ~~:gi:~GTH

::"
~
~

1.0

FREE AIR

Ie

1-

I<

0.125" LEAD LENGTH
FROM PC BOARD
FREE AIR

1.0

NO HEAT SINK

==

0.5

WITH 30'CfW HEAT SINK
I

0

15

30

45

60

I

I

0

75

AMBIENT TEMPERATURE JOCI

15

30

45

50

~VDUT·1IJ9m\l

":5....
~
....

2011

II

""

100

If

I<

=

I

300 r-- -Tj.III"C

.!

::"

I

0.1

0.1

==

r- 7-

j:

:.:~~Ep~DB~~~~TH .

0.5

--

5.0 ~INITE HEAT SINK=

z

t---

_

WITH 7Z"CfW HEAT SINK

Peak Output Current
400

75

.......

1

:-----.~

Tj"'5I1"C

I
I
5

0

AMBIENT TEMPERATURE I"CI

~~

Tj-2S'C

10

15

20

25

TUH/n44-4

Dropout Voltage

a

~

m
a

1.5

::"

1.0

i

0.5

....

""

Ripple Rejection

2.5
2.0

"
"
I
I~T
:70 ~±:±-t

I-F~

iii

Output Impedance

'OYT "1 , •0 jA
I

I

-=,...

i

60

"
:;

100

....

",N "'10V
lOUT .. 40mA

125

10

100

1.0
0.5

./

r..;~5"C

JUNCTION TEMPERATURE I"CI

5V

""

"oUT·5V

20

I

75

50

~
::"

I'

40

::

TA • 2rC
Cor::;
COUT :: 1~F TANTALUM'

Z

0
25

VOUT

lOUT =40mA

...

;;j
I<

I

'rloi' V~UT

§

z

"t;

OROPOUT CO~OJ,O~S - - i -

A, VOlT

V,N :: 10Y

5.0

BO

:!!

r- -+-J. 1 loUT "40 mA

r- f-

0

'0

'00

~

30

INPUT·OUTPUT DIFFERENTIAL (VI

0.1
lk

10k

10

lOOk

100

lk

FREQUENCV (Hzl

10k

lOOk

1M

FREQUENCV (Hz!
TLlH/n44-5

4.0

Quiescent Current

Quiescent Current
3.4

3.B

"ill....
.!

3.2
l.O

z

2.8

~:;

"

.!

3.4

I<

~
....

":5....

3.6

2.&
2.4

I<

3.0
2.9

I"

2.B

'"....
i:l

II
IL

VOUT " 5\1
lOUT -40 mA
T, -2lfC

2.2
2.0
5

10

15

20

25

lO

3.l
3.2
3.1

V,N -lOY

...........

C"-...
...........

"

2.7
2.B
2.5
2.0
0

INPUT VOLTAGE (VI

_

YOUT '" 5\1
lOUT =40mA-

25

50

75

~

100

"

125

150

JUNCTION TEMPERATURE I"CI
TLlH/7744-6

1-204

Equivalent Circuit
LM78LXX

..------------------------------------..------~--------_1~OV'N

r-----~-----R4
411

RII
1.9

L...--------------+---..--+-o Vou,

CI
5 pF

R12

RZ

].41k
RB
15k

R7

13k
01

02

RI
],B9.

RI]

2m

L-~~--~~-----4~-4~-4--------~~~--------------------------~~OGNO
TL/HI7744-7

Typical Applications
Fixed Output Regulator
INPUT ---4I~-I

Adjustable Output Regulator
INPUT ---4~--I

1--4",- OUTPUT

...._ . ._ . ._DUTPUT

CI*
D,33j.F

TLlH/7744-6

'Requlred If the regulator Is located more than 3" 'rom the power supply
filter.
•• See Note 4 in the electrical characteristics table.

TL/HI7744-9

VOUT = 5V
5V1Rl

1·205

+

(5V1Rl

+ 'a) R2

> 3 la. load regulation (L,) '" [(Rl +

R2)/Rlj (L, of LM7BL05)

Typical Applications (Continued)
Current Regulator

--"-04

INPUT

Rl

-

......- - - - . - - OUTPUT
lOUT

= (VOUT/Rl) +

lOUT

10

TUH/7744-10

> 10 = 1.5 rnA over line and load changes

5V, 500 mA Regulator with Short Circuit Protection
1.1

Y'N =10V

o-....~"',..,....._-"""
VOUT = 5V AT 500 mA

4.4

'Solid tantalum.
"Heat sink

TL/H/7744-11

01.

'''Optlonal: Improves ripple rejection and transient response.
Load Regulation: 0.6% 0 ,,; IL ,,; 250 rnA pulsed with toN

=

50 ms.

± 15V, 100 mA Dual Power Supply
+V'N = ZOV

o--...-t

1 - - - -...-o+VouT =15VAT100mA
C4
O.OI~F

-Y,N • -ZOV

.........- -...-0

0---4......

-VOUT' -15V AT 100 mA
TL/H/7744-12

Variable Output Regulator 0.5V-18V

I--~---+------~-~~VOUT

+

R4

~f
':" R5

30pF
TUH/7744-13

'Solid tantalum.
VOUT = VG
VOUT

=

+

5V. Rl = (- V'N"o LM78LOsl

5V (R2/R4) for (R2

+

R3)

=

(R4

A O.5V output will correspond to (R2/R4)

1-206

+

R5)

= 0.1

(R3/R4)

= 0.9

~National

~ Semiconductor

LM78MG
4-Terminal Adjustable Voltage Regulator
General Description

Features

The LM78MG is a 4-terminal adjustable positive voltage regulator that has an output voltage range between 5V and
30V. It is designed to operate with a maximum input voltage
of 40V and to deliver up to 500 mA of load current. Output
current capability can be increased to greater than 10A
through use of one or more external transistors.

•
•
•
•
•

Output current in excess of 0.5A
Output voltage adjustable from 5V to 30V
Internal thermal overload protection
Internal short circuit current protection
Output transistor safe-area protection

Connection Diagram and Ordering Information
(TO-202)
Plastic Package

-

-v-;

CONT
OUT

3
2
1

0

IN
COIAIA

~

COMM

TLlH/looSB-1

Top View
Heat sink tabs connected to comm through device substrate. Not recommended for direct electrical connection.

Order Number LM78MGCP
See NS Package Number P04A

(TO-39)
Metal Can

•

TL/H/IOOSB-23

Bottom View
Order Number LM78MGH/883
See NS Package Number HA04E
LM78MG Test Circuit 1
Vo

( RI

+

R2)

= """"""R2

VCONT Nominally

VCONT

OUTI-....-

....- VO

Rl

= 5V

0.1 J.lF

Recommended R2 current '" 1 mA
R2 = 5 kG

R2

TLlH/looSB-20

1-207

Absolute Maximum Ratings
If Military/Aerospace specified devices are reqUired,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Storage Temperature Range
-65°Cto + 150"C
Junction Temperature Range
LM7SMGC
O"C to + 150°C
LM7SMG
- 55°C to + 150°C

LM78MGC
Electrical Characteristics O°C :s:; TA :s:;
Co = 0.1 ,...F, Test Circuit 1, unless otherwise specified
Symbol

Parameter

Lead Temperature (Soldering, 10 sec.)
Internal Power Dissipation
Input Voltage
Control Lead Voltage

125°C for LM7SMGC, VI

=

10V, 10

Conditions (Notes 1, 2)

Input Voltage Range

TJ

VOUT

Output Voltage Range

VI

Vo

Output Voltage Tolerance

(Vo + 3.0V) :s:; VI :s:; (Vo + 15V),
5.0 rnA :s:; 10 :s:; 350 mA,
Po :s:; 5.0W, VI Max = 3SV

350 rnA, CI

Min

= 25°C
= Vo +5.0V

VIN

=

TJ

265°C
Internally Umited
+40V
OV:S:; Vo:S:; Vo

Typ

=

0.33 ,...F,

Max

Unlta

7.5

40

V

5.0

30

V

= 25°C

4.0
5.0

% (Vo)

AVO/AVIN

Line Regulation

TJ = 25°C,10 = 200 rnA, Vo :s:; 10V,
(Vo + 2.5V) :s:; VI :s:; (Vo + 20V),

1.0

%(Vo)

AVo/AILOAO

Load Regulation

TJ = 25°C, 5.0 rnA :s: 10 :s: 500 rnA,
VI = Vo +7.0V

1.0

%(Vo)

Ie

Control Lead Current

TJ

= 25°C

1.0

6.0

,...A

7.0
IQ

Quiescent Current

TJ

= 25°C

2.S

5.0

rnA

6.0
AVIN/AVOUT

Ripple Rejection

10 = 125mA,S.OV:S: VI:S: ISV,
Va = 5.0V, f = 2400 Hz
10 Hz:s: f :s: 100 kHz, Vo

en

Output Noise Voltage

VIN-VOUT

Dropout Voltage
(Note 3)

Iso

Short Circuit Current

Ipk

Peak Output Current

AVo/AT

Average Temperature
Coefficient of Output
Voltage

Ve

Control Lead Voltage
(Reference)

62

= 5.0V

= 35V, TJ = 25°C
TJ = 25°C
Vo = 5.0V,
TA = O"Cto +25°C
10 = 5.0 rnA TA = 25°C to 125°C

SO
S

40

,...VIVO

2

2.5

V

600

rnA

1.4

A

VI

TJ

= 25°C

0.4

O.S

0.4
0.3
4.S
4.75

1-20S

dB

5.0

5.2
5.25

mVloCI
Vo
V

LM78MG
Electrical Characteristics
Co

=

-55°C,;;; TA ,;;; 125°C for LM78MG, VI
0.1 p.F, Test Circuit 1, unless otherwise specified (Note 6).

Symbol

Parameter
TJ

Output Voltage Range

VI

Vo

Output Voltage Tolerance (Vo + 3.0V) ,;;; VI ,;;; (Vo + 15V),
5.0 rnA ,;;; '0 ,;;; 350 rnA,
PD ,;;; 5.0W, VI Max = 38V

AVo/AILOAD Load Regulation
Control Lead Current

Ie

=

350 rnA, CI

=

0.33 p.F,

Min Typ Max

= 25°C
= Vo +5.0V

Input Voltage Range

VOUT

Line Regulation

10V, 10

Conditions (Notes 1, 2)

VIN

I:No/AVIN

=

TJ

=

Units

7.5

40

V

5.0

30

V

4.0

25°C

5.0

% (Vo)

TJ = 25°C,lo = 200 rnA, Vo ,;;; 10V,
(Vo + 2.5V) ,;;; VI ,;;; (Vo + 20V),

1.0

% (Vo)

TJ = 25°C, 5.0 rnA,;;; '0 ,;;; 500 rnA,
VI = Vo +7.0V

1.0

%(Vo)

TJ

=

1.0

25°C

6.0

p.A

7.0

'0

Quiescent Current
(Note 5)

AVIN/AVOUT Ripple Rejection
en

Output Noise Voltage

VIN-VOUT

Dropout Voltage
(Note 3)

Ise

Short Circuit Current

TJ

=

7.0

rnA

8.0
10 = 125 rnA, VI = 10V,
Vo = 5.0V, f = 2400 Hz
10 Hz';;; f,;;; 100 kHz, Vo

60

=

5.0V

= 35V, TJ = 25°C
TJ = 25°C, VI = 12V (Note 4)

80

'pk

Peak Output Current
Average Temperature
Coefficient of Output
Voltage

Vo = 5.0V,
10 = 5.0 rnA

Control Lead Voltage
(Reference)

TJ

=

0.4

=
TA =
TA

40

p.VlVo

2

2.5

V

600

rnA

1.4

A

0.8

O"Cto +25°C

0.4

25°C to 125°C

0.3
4.8

25°C

dB

8

VI

AVo/AT

Ve

2.8

25°C

4.75

5.0

5.2

mVrC/
Vo
V

5.25

.
Al + A2
Note 1: Vo,sdefinedasVo = ~(5.0).

Note 2: All characteristics except noise voltage and ripple rejection retio are measured using pulse techniques (tw s; 10 mo. duty cycle s; 5%). Output voltage
changes due to changes in Internal temperature must be taken into account separately.
Note 3: Dropout voltage is defined ao that input/output voltage differential which causeo the output voltage to decrease by 5% of its innial value.
Note 4: The peak output current is defined as the output current when VOUT is equal to 90% of its nominal value.
Note 5: This measurement includes 1 mA provided to the output resistors.
Note 6: A military AETS electrical test opacification io available on request. At the time of printing, the LM78MGH AETS specification complied fully with the limits in
the table on this page.

1-209

Typical Performance Characteristic
Peak Output Current
vs Input/Output
Differential Voltage

Quiescent Current
vs Input Voltage

Control Current
vs Temperature

1.4

--

1.2

~

§
tl

I

1.0
O.B

/I

O.B

l'

....

TJ -= OOC

tl
2.0

~

i:i5
'"

.......... .....

0.2

01:1 • V
~=100mA

5

10

15

20

25

3D

10

15

INPUT/OUTPUT DIFFERENTIAL (V)

'>'

I

12 10

=500 mA

8
~

I"

'/

!!!

6

8
~

i"

V

2

TJ = 125°
0
5

10

15

"

20

25

-2.5

~~

I

4

30

-5.0

..... 1'-..

-10.0

I
~

~

2.0

r-

1.5

I

1.0

.. §

\'~/OOmA

3
z

~
~

125

'"

2Q

~~

10

~

~

~

~.

~

600

800

" "~

60
55
50
5

100

10k

lk

\!

1

!:;
~

0

I

-1

lOOk

mA
8

8

10

.5
~
ill
tl

OUTPUT VOLTAGE
DEVIATION

Q

g

V, = 10V
-2 Vo =5.0
0

10

20

30

40

50

80

TIME (".)

100

30
IT
AD
20
INFINITE HEAT SIN r10
5.0
'h~,o ~
4.0
3.0
°c/< ....
2.0
1.0
INOH£J,TS~
"
D.5
D.4
D.3 BJC' 12 0 ci~.:
0.2 ""(WAX) = 7.5W
0.1
50
75
100
125
25

-5

~

0

15

0

30

1

LOAD CU RENT

2

20

5

-20 Vo = 5.0V
4

25

Worst Case Power Dissipation
vs Ambient Temperature

~

~

~

>

~

i!!

~
z

~

ill2i

i

Q

2

20

2

3

FREQUENCY (Hz)

0=5

15

Load Transient Response

t~~~~;ill

10

0

10

OUTPUT VOLTAGE (V)

~

OUTPUT VOLTAGE
DEVIATION

150

N.

0

~

INPUT VOLTAGE

-10

125

10 = 200 mA

65

1000

£

10

0

......

100

4

40

!C

~

r-...

,II

150

75

45 TJ =25 0 C

400

Line Transient Response
30

70

'"

JUNCTION TEMPERATURE (OC)

!

75

~

V, = 8.0V TO 18V
20 VO=5.0V
0

100

3

40

AVO = 5" OF Vo

75

...... r-... TJ =25 C
r-...

'iii'

60

iil

roo

~1~20"lAj'"1'DROPOUT CONDITlOjS -I I
50

50

N--I.

80

80

'iii'

25

85

V, = 10V
= 5.0V

,0

Ripple Rejection
vs Frequency

0
0

25

Ripple Rejection
vs Output Voltage

100

~

~

0

-17.5
-20.0
200

I"-

=

OUTPUT CURRENT (mA)

.l5100-k

t-

35

-15.0

I

'>'

I'
V, = 10
Vo = 5.0V:
10 350 mA

TEMPERATURE (Oc)

-12.5

Dropout Voltage vs
Junction Temperature

.5

0.5

o

0

-7.5

INPUT VOLTAGE (V)

2.5

3D

25

0.0

'>'

~

!!!

I

\

Differential Control Voltage
vs Output Current

.5

10 Vo a 5.0V

8

20

itl

INPUT VOLTAOE (V)

Differential Control Voltage
vs Input Voltage

.5

\
1.0

=25°C

J

1.0
5

0
0

~

.3

§

......... :-

TJ = 25°C

J=2~"'"

0..4

1.5

3.0

~

.5

I I I I I

is

~oc/w

-

1i

I ....
I

-10
12

TINE (1'.)

150

AMBIENT TEMPERATURE (OC)

TLlHI1 0058-5

1·210

riii:

.....

LM78MG Equivalent Circuit

CI)

iii:

C)

IN

02
Q16
R21
6804
Rll
0.6 k4

R17
2004

OUT
CONTROL

~--~~--~--~----~---o--------~--~~----~-------------------COMMON

TL/H/100SB-3

Design Considerations
The LM78MGC variable voltage regulator has an output
voltage which varies from VCONT to typically
(Rl + R2)
VI - 2.0V by Vo = VCONT
R2

To calculate the maximum junction temperature or heat sink
required, the following thermal resistance values should be
used:
Package

The nominal reference voltage of the LM78MG is 5.0V. If we
allow 1.0 mA to flow in the control swing to eliminate bias
current effects, we can make R2 = 5 k!l in the LM78MG.
The output voltage is then: Vo = (Rl + R2) Volts, where
R1 and R2 are in k!ls.
Example: If R2 = 5.0 k!l and Rl = 10 k!l then
Vo = 15V nominal, for the LM78MGC.
By proper wiring of the feedback resistors, load regulation of
the device can be improved significantly.
The LM78MGC regulator has thermal overload protection
from excessive power, internal short circuit protection which
limits the circuit's maximum current, and output transistor
safe-area protection for reducing the output current as the
voltage across the pass transistor is increased.
Although the internal power dissipation is limited, the junction temperature must be kept below the maximum specified temperature in order to meet data sheet specifications.

Power Watt

Max
OJC

Typ

OJC

OJA

Max
OJA

8.0

12.0

70

75

Typ

P
_ TJMax-TA
DMax - OJC + OCA or
TJ Max - TA (without a heat sink)
OJA
OCA = Ocs + OSA
Solving for TJ:
TJ = TA + PD(OJC + OcAl or
TA + POOJA (without heat sink)
Where
TJ = Junction Temperature
TA = Ambient Temperature
Po = Power Dissipation
OJC = Junction-to-Case Thermal Resistance
OCA = Case-to-Ambient Thermal Resistance
OCS = Case-Io-Heat Sink Thermal Resistance
OSA = Heat Sink-to-Ambient Thermal Resistance
OJA = Junction-Io-Ambient Thermal Resistance
1-211

Typical Applications
Positive High Current
Short Circuit Protected Regulator

Bypass capacitors are recommended for stable operation of
the LM78MG over the input voltage and output cilrrent
ranges. Output bypass capacitors will improve the transient
response of the regulator.
The bypass capacitors, (0.33 ,..F on the input, 0.1 ,..F on the
output) should be ceramic or solid tantalum which have
good high frequency characteristics. The bypass capacitors
should be mourited with the shortest leads, and if poSSible,
directly across the regulator termimils.

Rsc

I-<--.. . . .

-~VO

10 Max

0.1 }.IF

Nate 1: All resistor values in ohms.

Basic poslilve Regulator

OUT I - - t - -....-+Vo

TL/H/l0058-14

Lt.178t.1G
Rl

0.1 J.lF

= .6VSE 01 + .610 Max Rsc
.6 IAMax- lo Max

0.33J.1F

Positive Hlgh·Current Voitage Regulators

+vl-l-.r;IN~~O~UTa.-....J

TL/H/l0058-8

LM78MG

+Vo

CONTROL
COMMON

D.33J.1F

Positive 5.0V to 30V Adjustable Regulator

..............- ...-+Vo

0.1 J.lF
TUHI10058-12

External Series Pass (a)

+VI -

TL/HI10058-9

....--IIN

OUT I - -...__-r

LM78MG

Positive 5.0V to 30V
Adjustable Regulator 10 > 1.5A

CONTROL
COMMON

1>1.5A_

Ql

Rsc
L..._-,"-o+VO

2N6124

RI
Rl

...............- ...-+Vo

en

R2

+32V~""'W~"""'-I
D.l }.IF

TL/HI1005B-15

External Series Pass with Short·Clrcuit Limit (b)

TUHI10058-10
Rl

=

.6 VSE(OI)
iliA Max-Io Max

Nate: External series pass device Is nol short clrcutt protected.

TUH110058-13

Current Limit Graph

1-212

,-------------------------------------------------------------------------, r
s:
.......

~National

CD

s:

~ Semiconductor

><
><
~

LM79MXX Series
3-Terminal Negative Regulators

::::!.

m

General Description
The LM79MXX series of 3-terminal regulators is available
with fixed output voltages of -SV, -8V, -12V,and -1SV.
These devices need only one external component-a compensation capacitor at the output. The LM79MXX series is
packaged in the TO-202 power package, TO-220 power
package, and TO-39 metal can and is capable of supplying
O.SA of output current.
These regulators employ internal current limiting, safe area
protection, and thermal shotdown for protection against virtually all overload conditions.
Low ground pin current of the LM79MXX series allows output voltage to be easily boosted above the preset value with
a resistor divider. The low quiescent current of these devices with a specified maximum change with line and load ensures good regulation in the voltage boosted mode.

For outputvoltage other than -SV, -8V, -12V, and -1SV
the LM137 series provides an output voltage range from
-1.2V to -S7V.

Features
•
•
•
•

Thermal, short circuit and safe area protection
High ripple rejection
O.SA output current
4% tolerance on preset output voltage

Connection Diagrams
TO·202 Plastic Package (P)
INPUT

!
TL/H/l0483-5

Front View

Order Number LM79M05CP, LM79M12CP or LM79M15CP
See NS Package Number P03A

<

TO·39 Metal Can Package (H)

GNO

{

/?

U

TO·220 Plastic Package (T)

OUTPUT

OUTPUT
INPUT

INPUT
• . ~ (CASE)

GROUND
TL/H/l04B3-7

Front View
TLlH/l0483-6

8ottomVIew
Order Number LM79M05CH, LM79M08CH,
LM79M12CH or LM79M15CH
See NS Package Number H03A

1-213

Order Number LM79M05CT, LM79M08CT,
LM79M12CT or LM79M15CT
See NS Package Number T038

•

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Vo = -5V
Vo = -BV, -12V, -15V

-25V
-35V

Input/Output Differential
VO= -5V
Vo= -BV,-12V,-15V

25V
30V

Power Dissipation (Note 2)

Internally Limited

Operating Junction Temperature Range
Lead Temperature (Soldering, 10 sec.)

TBD

Electrical Characteristics LM79M05C, LM79M08C
Part Number

LM79M05C

+ 125'C
LM79M08C

Output Voltage

-5V

-8V

Input Voltage (Unless Otherwise Specified)

-10V

-14V

Vo

Parameter
Output Voltage

Conditions
TJ

= 25'C

5 rnA ,;; lOUT';; 350 mA

l!.Vo

Line Regulation

TJ

Min

Typ

Max

-4.8

-5.0

-5.2

-4.75
-5.25
(-25';; VIN ,;; -7)

= 25'C (Note 3)

l!.Vo

Load Regulation

TJ = 25'C, (Note 3)
5 mA ,;; lOUT';; 0.5A

10

Quiescent Current

TJ

l!.lo

Quiescent Current
Change

With Input Voltage

50
B
(-25';; VIN';; -7)
2
30
(-18,;; VIN ,;; - 8)

= 25'C

lOMAX

Units

Min

Typ

Max

-7.7

-8.0

-8.3

V

-7.6
-8.4
(-25';; VIN ,;; -10.5)

V

5
80
(-25';; VIN ,;; -10.5)
3
50
(-21 ,;; VIN ,;;. -11)

mV
mV

30

100

30

160

mV

1

2

1.5

3

mA

0.4

0.4
(-25';; VIN';; -10.5)

mA

0.4

0.4

mA

(-25';; VIN';; -8)
With Load,
5mA,;; lOUT';; 350mA

Vn

+ 125'C
+ 150'C
230'C

ESD Susceptability

Conditions unless otherwise noted: lOUT = 350 mA, CIN = 2.2 ""F, COUT = 1 ""F, O'C ~ T.i ~

Symbol

O'C to
-65'Cto

Storage Temperature Range

Output Noise Voltage

TA = 25'C,
10Hz,;;l,;; 100Hz

Ripple Rejection

1 = 120Hz

Dropout Voltage

TJ

1.1

V

TJ

800

800

mA

Average Temperature
Coefficient 01
Output Voltage

= 25'C,IOUT = 0.5A
= 25'C
lOUT = 5mA,

1.1

Peak Output Current

O'C ,;; TJ ,;; 100'C

-0.4

-0.6

mvrc

150
54

66
(-18';; VIN';; -8)

1·214

250

54
66
(-21';; VIN';; -11)

/LV
dB

....a::::

Electrical Characteristics LM79M 12C, LM79M 15C
Conditions unless otherwise noted: lOUT

=

350 mAo C'N

=

2.2 ....F. COUT

Part Number

=

1 ....F.O'C ,;; TJ ,;;

LM79M12C
-12V

-15V

Input Voltage (Unless Otherwise Specified)

-19V

-23V

Vo

fWo

Parameter
Output Voltage

Line Regulation

Conditions

Load Regulation

(/)

Units

Min

Typ

Max

Min

Typ

Max

TJ = 25'C

-11.5

-12.0

-12.5

-14.4

-15.0

-15.6

V

5 mA ,;; lOUT';; 350 mA

-11.4

-12.6

-14.25

-15.75

V

TJ = 25'C (Note 3)

(-27,;; V,N';; -14.5)

(-30';; VIN ,;; -10.5)

80
5
(-30';; VIN';; -14.5)

5
80
(-30';; VIN ';;-17.5)

3

f!..vo

><
><

LM79M15C

Output Voltage

Symbol

Ctj
a::::

+ 125'C

Quiescent Current

TJ = 25'C

Quiescent Current

With Input Voltage

Change

mV

240

mV

3

mA

0.4

mA

(-28';; VIN ,;; -18)

30

240

30

3

1.5

5 mA ,;; lOUT';; 0.5A

Il.lo

50

3

(-25';; VIN ,;; - 15)
T J = 25'C. (Note 3)

10

50

1.5

0.4
(-30';; VIN ,;; -14.5)

mV

(-30';; VIN ,;; -27)

With Load,
0.4

5 mA ,;; lOUT';; 350 mA
Vn

lOMAX

Output Noise Voltage

TA = 25'C.
10Hz';; I,;; 100Hz

Ripple Rejection

1 = 120 Hz

0.4

400
54

70
(-25,;; VIN ,;; -15)

54

mA

400

",V

70

dB

(-30';; VIN';; -17.5)

Dropout Voltage

TJ = 25'C, lOUT = 0.5A

1.1

1.1

V

Peak Output Current

TJ = 25'C

800

800

mA

Average Temperature

lOUT = 5mA.
O'C,;; TJ ,;; 100'C

-0.8

-1.0

mV/,C

Coefficient 01
Output Voltage

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but do not guarantee specific performance limits. For guaranteed speCifications and test conditions, see the Electrtcal Characteristics.
Note 2: Refer to Typical Performance Characteristics and Design Considerations for details.

Note 3: Regulation is measued at a constant iunction temperature by pulse testing with a low duty cycle. Changes in output voltage due to heating effects must be
taken into account.

1-215

CD

:::3.

m

Typical Performance Characteristics
Output Voltage vs
Temperature
~

~

1.01
1.005
1.00

i :::
~

~

§:

I

Ripple Rejection
100

I
...,.....,

I

-;:
-3

VOUT II -8V, -f2V, -1SV

~

i:l

-

1.01
1.005
1.00
o.tl5
o.tlO
-50 -25 0

i

I-

vour" -5V

'.'."",

vour'-Bv'K~
CoJr=

~5V

BO

~

O.lk

1.2
1.15

.1·

I"

TJII 125°C

~

/

-

TJ= DoC

o

0.1

0.2

~

ffi

5

1.1

it;
~

Ik

1.05

0.4

TJ• 125°C

.-

0.95

0.5

lOOk

1M

Quiescent Currant vs
Losd Current

i;"

i

1.0

10k

FREQUENCY (Hz)

TJ 2SjC

;

0.9
0.3

,.

I
~O

10 IS 20 25 30 35
INPUT VOLTAGE (V)

~
8
~

II!

..~

1.4

I
I

LM7IMOS

1.3
1.2

TJI'DOC

1.1

TJi2SDC

1:=

1.0
0.9

TJ =1 125DC

O.B

f--

I
0.1

0.2

0.3

0.4

0.5

OUTPUT CURRENT (A)

Maximum Average Power
Dissipation (TO·220)
20.--'--~---r--.---'

1.50

t:

O.Olk O.lk

lOOk

.5

Short-Circuit Current

i

10k

'C'

OUTPUT CURRENT (A)

3

Ik

LM79MOS

1.25

.5
T .25 0 C

~ --

!!i

Cour"'OIA F
SOLID TANTALUM
11)"2

Quiescent Current vs
Input Voltage
'C'

I.~

f

10"1

1.3

2.2
2.0
I.B
1.6
1.2
1.0
O.B
0.6
0.4

~

6

FREQUENCY (Hz)

2.~

§:

100

l!

~

Minimum Input-Output
Differential

!:i

:s
~

~o

JUNCTION TEMPERATURE (DC)

g
..,

10'

~

1s
....

60 Vour =-5V

20
o.olk

25 50 75 100 125 150

Output Impedance

v,N-vour' 5V
=25 0 C
llAF
SOLID TANTALUM

Maximum Average Power
Dissipation (TO-39)
3,--,--,---,--,--,

IBr-~r-~r-~--~---;

1.25
1.0
0.75
0.50

16~-+--~--r--+--~

:: ~ ~
TJ II 25°C

14
10~~r-~~~--~---;

~

TJ = 12f"C

l""1li

0.25

o
o

5

12r-~~~r-~--~---;

Tl = OOC

"

10 15 20 25 30 35

25

~O

50

75

100

125

AMBIENT TEMPERATURE (DC)

IV,N-Vourl (V)

25

50

75

100

125

AMBIENT TEMPERATURE (DC)

Maximum Average Power
Dissipation (T00202)
10
9

I
I

INFIN:TE

10DC/W HEAT
" SINK,

'\..

~

~

"

I~

" '\..

........

20 DC/j HEAT1SINK

o
o

25

HEA~ SINK

50

'"

~ [\.
~
75

100

125

AMBIENr TEMPERATURE (DC)
TL/H/l0483-10

1-216

ris:

Schematic Diagrams

.....a
CD

-5V

is:

><
><
en
CD

':'

::::1.
R18
4k

CD

R19
5k

til

R17
5.4k

. - - - -.....-1..--0 VOUT
OJ
6.2V

alJ
R20
20k
R4
20k
RJ

R21 R16

6k

150 0.05

V'No-~-~-~---6-~"-~~--~--------4--~------------~
TUH/l0483-8

-BV, -12Vand -15V

R18

R19

4k

5k

R17
11.7k (BV)
2D.lk (12V)
2B.4k (15V)

./'--t-....- < ) VOUT
OJ
6.2V

V,No-~-__~---4~~--+--~-------~..-~~----------~
TUH/l0483-9

1-217

Design Considerations

Typical Applications

The LM79MXX fixed voltage regulator series have thermaloverload protection from excessive power, internal short-circuit protection which limits the circuit's maximum current,
and output transistor safe-area compensation for reducing
the output current as the voltage across the pass transistor
is increased.

Bypass capacitors are necessary for stable operation of the
LM79MXX series of regulators over the input voltage and
output current ranges. Output bypass capacitors will improve the transient response of the regulator.
The bypass capacitors (2.2 p.F on the input, 1.0 p.F on the
output), should be ceramic or solid tantalum which have
good high frequency characteristics. If aluminum electrolytics are used, their values should be 10 p.F or larger. The
bypass capacitors should be mounted with the shortest
leads, and if pOSSible, directly across the regulator terminals.
Fixed Regulator

Although the internal power dissipation is limited, the junction temperature must be kept below the maximum specified temperature in order to meet data sheet specifications.
To calculate the maximum junction temperature or heat sink
required, the following thermal resistance values should be
used:
6JC

6JA

rC/W)

rC/W)

TO-39

16

120

TO-202

12

70

TO-220

3

40

Package

POMAX = TJMax - TA or
6JC + 6CA

1-.....-0 OUTPUT
TL/H/10483-2

"Required if regulator is separated from filter capacitor by more than 3" .
For value given, capaCitor must be solid tantalum. 25 ""F aluminum electrolytic may be substituted.

(1)

tRequired for stability. For value given. capacitor must be solid tantalum.
25 f'F aluminum electrolytic may be substituted. Values given may be
Increased without limit.

= TJMax - T A (Without a Heat Sink)
6JA

For output capacitance in excess of 100 f'F. a high current diode from
input to output (IN4001. etc.) will protect the regulator from momentary
input shorts.

6CA = 6cs + 6SA
Solving for TJ:
TJ = TA + Po (6JC + 6CA) or
= T A = + P06JA (Without a Heat Sink)
Where
TJ
= Junction Temperature
T A = Ambient Temperature
Po
= Power DisSipation
6JC = Junction-to-Case Thermal Resistance
6CA = Case-to-Ambient Thermal Resistance
6cs = Case-to-Heat Sink Thermal Resistance
6SA = Heat Sink-to-Ambient Thermal Resistance
6JA = Junction-to-Ambient Thermal Resistance

Variable Output

Cl
2.2}'F
SOLID
TANTALUM
INPUT 0-.....---1

1--.....- _......0

OUTPUT

TL/H/10483-3

"Improves transient response and ripple rejection.
Do not increase beyond 50 f'F.

+ R2)
A2

Rl
VOUT = VSET (

Select R2 as follows:
LM79M05C
300n
LM79M08C
soon
LM79M12C
750n
LM79M15C
lk

1-216

!i:....

Typical Applications (Continued)

CD

3:

± 15V, 1 Amp Tracking Regulators
+VINo----I
1
1
1
1
1
1

----P--.. . .--.. . -<>

t--.....

Your +15V

:::!.

R4*
10k
1%

CD

(II

01
lN4001

C4** ~
25J'F

><
><
en
CD

T

RS*
10k
1%

....---p--....-t------t-+--.....--o COMMON
1
1

C5**~
25J'F

02

T

lN4001

1
I

t--....----------+-<> Your -15V
TL/H/l0483-1

Load Regulation at 0.5A
Output Ripple, CIN = 3000 fJ.F, IL
Temperature Stability
Output Noise 10 Hz,,; f ,,; 10 kHz

= 0.5A

Performance (Typical)
(-15)
(+15)
40mV
2mV
100fJ.Vrms
100 fJ.Vrms
50mV
50mV
150fJ.Vrms
150 fJ.Vrms

·Resistor tolerance of R4 and RS determine
malching of (+) and (-) outputs.
•• Necessary only if raw supply filter capacitors
are more than 311 from regulators.

Dual Trimmed Supply

+INPUT 0--1.......

1---1_-1-----1_-0 +5.0V
....---'Wlr-t~< 1k

01
lN4001

o-~~---+------~~-+--~----.--oroM

02

IN4001

INPUT

--..-----4.....-o

t----+--.....

II

-5.0V
TL/H/l0483-4

1·219

.------------------------------------------------------------------,
:!I" ~National
~

~

m

~ Semiconductor

LM79XX Series 3-Terminal Negative Regulators
General Description
The LM79XX series of 3-terminal regulators is available with
fixed output voltages of -5V, -8V, -12V, and -15V.
These devices need only one external component-a compensation capacitor at the output. The LM79XX series is
packaged in the TO-220 power package and is capable of
supplying 1.5A of output current.
These regulators employ internal current limiting safe area
protection and thermal shutdown for protection against virtually all overload conditions.
Low ground pin current of the LM79XX series allows output
voltage to be easily boosted above the preset value with a
resistor divider. The low quiescent current drain of

these devices with a specified maximum change with line
and load ensures good regulation in the voltage boosted
mode.
For applications requiring other voltages, see LM137 data
sheet.

Features
•
•
•
•

,moo::,

Thermal, short circuit and safe area protection
High ripple rejection
1.5A output current
4% tolerance on preset output voltage

Connection Diagrams

TO-3 Package

TO-220 Package
INr T
OUTPUT

0

GNO><

INPUT

0
TL/HI7340-10

GROUND
TL/H17340-14

SottomVlew

Front View

Order Number LM7905CK, LM7908CK, LM7912CK or
LM7915CK
See NS Package Number KC02A

Order Number LM7905CT, LM7908CT, LM7912CT or
LM7915CT
See NS Package Number T03S

Typical Applications
Fixed Regulator
'Required if regulator is separated from filter capacitor by
more than 3". For value given, capaCitor must be solid
tantalum. 25 p.F aluminum electrolytic may be substituted.
tRequired for stability. For value given, capacitor must be
solid tantalum. 25 p.F aluminum electrolytic may be substituted. Values given may be increased without limit.
TL/H/7340-3

1-220

For output capaCitance in excess of 100 p.F, a high current
diode from input to output (1 N4001, etc.) will protect the
regulator from momentary input shorts.

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
(Vo = -5V)
-25V
(Vo = -avo -12V. and -15V)
-35V

Input-Output Differential
(110 = -5V)
25V
(Vo = -av, -12V -and 15V)
30V
Internally Limited
Power Dissipation (Note 2)
Operating Junction Temperature Range
O'C to + 125'C
Storage Temperature Range
-65'Cto + 150'C
Lead Temperature (Soldering, 10 sec.)
230'C

Electrical Characteristics Conditions unless otherwise noted: lOUT =
O'C ,;: TJ ,;:

Symbol

+ 125'C, Power Dissipation';:
Part Number

LM7905C

Output Voltage

-5V

-BV

Input Voltage (unless otherwise specified)

-10V

-14V

Parameter
Output Voltage

Vo

Conditions
TJ = 25'C
5 mA ,;: lOUT
P s: 15W

s:

I

Min

lA,

TJ = 25'C, (Note 3)

AVO

Load Regulation

TJ = 25'C, (Note 3)
5 mA,;: lOUT s: 1.5A
250 mA ,;: lOUT';: 750 mA

15
5
1

10

Quiescent Current

TJ = 25'C

Quiescent Current
Change

With Line

s:

lOUT

Output Noise Voltage TA = 25'C, 10Hz';: f
Ripple Rejection

lOMAX

Max

s:

s:

s: VIN s:

lA

100Hz

f=120Hz

s:

I

Typ

Max

5
80
(-25';: VIN';: -10.5
3
30
(-17';: VIN';: -11)

mV
V
mV
V

100
50

15
5

200
75

mV
mV

2

1.5

3

mA

0.5
-7)
0.5

66
VIN ,;: -8)

0.5
(-25';: VIN ,;: -10.5)
0.5

mA
V
mA

200

p.V

54
60
(-21';: VIN';: -11)

dB
V
V

Dropout Voltage

TJ = 25'C, lOUT = lA

1.1

1.1

Peak Output Current

TJ = 25'C

2.2

2.2

A

0.4

-0.6

mV/'C

Average Temperature lOUT = 5mA,
Coefficient of
OC s: TJ';: 100'C
Output Voltage

Typical Applications

(Continued)
Variable Output

CI
2.2.F -

+

J.:.CJo
-r=2s"F

INPUT

L.;

~

HI

H2
I
J: LM19X XCT : 2

~
C2
_ .!.I.F

....

SOll~T

TANTALUM

T

- TANTALUM

soliO

OUTPUT
TL/H/7340-2

·Improves transient response and ripple rejection. Do not increase beyond 50 J-LF.
VOUT

I

V
V
V

125
54
(-18

Min

Units

-7.7
-8.0
-8.3
-8.4
-7.6
(-23';: VIN ,;: -10.5)

8
50
(-25';: VIN ,;: -7)
15
2
(-12';: VIN ,;: -8)

(-25
With Load, 5 mA

I

Typ

Line Regulation

Ala

LM790BC

-5.0
-4.8
-5.2
-4.75
-5.25
(-20 s: VIN s: -7)

AVO

Vn

500 mA, CIN = 2.2 /-LF, COUT = 1 /-LF,

1.5W.

+ R2)
= VSEl (RI
"""""R2

Select R2 as follows:
LM7905CT
300n
LM790SCT
soon
LM7912CT
750n
LM7915CT
Ik

1-221

II

Electrical Characteristics
COUT

Symbol

=

(Continued) Conditions unless otherwise noted: lOUT
1.5W.

+ 125°C, Power Dissipation =

1 ,..F,O"C ,,; TJ ,,;

500 mA, CIN

Part Number

LM7912C

LM7915C

Output Voltage

-12V

-15V

Input Voltage (unless otherwise specified)

-19V

-23V

Parameter

Conditions

Min

Vo

Output Voltage

TJ = 25°C
5mA,,; lOUT"; 1A,
p,,; 15W

AVo

Line Regulation

TJ

AVo

Load Regulation

TJ = 25°C, (Note 3)
5 mA,,;; lOUT"; 1.5A
250 mA ,,;; lOUT";; 750 mA

=

=

25°C, (Note 3)

10

Quiescent Current

TJ

Ala

Quiescent Current
Change

With Line

Vn

Output Noise Voltage

TA

Ripple Rejection

1 = 120 Hz

Dropout Voltage

TJ

Peak Output Current

TJ

=

=
=

J Typ 1 Max

=

I

Typ

2.2 ,..F,

Units

I

Max

-14.4 -15.0 -15.6
-14.25
-15.75
(-30"; VIN"; -17.5)

V
V
V

5
80
(-30"; VIN"; -14.5)
30
3
(-22";; VIN ,,;; -16)

5
100
(-30"; VIN"; -17.5)
50
3
(-26"; VIN ";;-20)

mV
V
mV
V

15
5

200
75

15
5

200
75

mV
mV

1.5

3

1.5

3

mA

0.5
(-30";; VIN ,,; -14.5)
0.5

25°C,10Hz,,; 1,,; 100Hz

25°C, lOUT

Min

=

-11.5 -12.0 -12.5
-11.4
-12.6
(-27"; VIN ,,; -14.5)

25°C

With Load, 5 mA ,,; lOUT"; 1A

lOMAX

=

0.5
(-30 ,,;VIN"; -17.5)
0.5

mA
V
mA

300

375

,..V

54
70
(-25"; VIN"; -15)

54
70
(-30"; VIN"; -17.5)

dB
V

1.1

1.1

V

2.2

2.2

A

1A

25°C

mVioC
-0.8
-1.0
Average Temperature lOUT = 5mA,
OC,,;TJ";10o-C
Coefficient 01
Output Voltage
Note 1: Absolute Maximum Ratings Indicate limits beyond which damage to the device may occur. Operating Ratings indicate condHions for which the device Is
Intended to be functional. but do not guarantee Specific Perfonnance limits. For guaranteed specifications and test conditions. see the Electrical Characteristics.
Note 2: Refer to Typical Performance Characteristics and Design Considerations for details.
Note 3: Regulation Is measured at a constant lunction temperature by pulse testing wHh a low duty cycle. Changes in output voltage due to heating effects must be
taken into account.

Typical Applications (Continued)
Dual Trimmed Supply
+5.0Y

+,NPUTo-M LM340-5 :OUT
GNO
240

0.22}1F:~

Dl

1k

~ II. lN4001

33
COM

+
2.2 }IF: ::

33
470
5k

!'}1F "" 02
.oil II. lN4001

GNO

-INPUT 0-

~

LM7905

I

-5.0Y

lOUT

TLlHI7340-4

1-222

r:s:::
.....

Design Considerations

CD

The LM79XX fixed voltage regulator series has thermal
overload protection from excessive power dissipation, internal short circuit protection which limits the circuit's maximum current, and output transistor safe-area compensation
for reducing the output current as the voltage across the
pass transistor is increased.

Where:

Although the internal power dissipation is limited, the junction temperature must be kept below the maximum specified temperature (125'C) in order to meet data sheet specifications. To calculate the maximum junction temperature or
heat sink required, the following thermal resistance values
should be used:

Package

Typ

Max

Typ

Max

OJC

OJC

OJA

OJA

'C/W

'C/W

'C/W

'C/W

TO-3

3.5

5.5

40

35

TO-220

3.0

5.0

60

40

TJ

= TA

= Ambient Temperature

PD

= Power Dissipation

OJA

= Junction-to-Ambient Thermal Resistance

OJC

= Junction-to-Case Thermal Resistance

Ocs

= Case-to-Heat Sink Thermal Resistance

0SA = Heat Sink-to-Ambient Thermal Resistance

Typical Applications (Continued)
Bypass capacitors are necessary for stable operation of the
LM79XX series of regulators over the input voltage and output current ranges. Output bypass capacitors will improve
the transient response by the regulator.
The bypass capacitors, (2.2 ,u.F on the input, 1.0 ,u.F on the
output) should be ceramic or solid tantalum which have
good high frequency characteristics. If aluminum electrolytics are used, their values should be 10 ,u.F or larger. The
bypass capacitors should be mounted with the shortest
leads, and if pOSSible, directly across the regulator terminals.

+ OSA (without heat sink)

Solving for TJ:
TJ = TA

TA

OCA = Case-to-Ambient Thermal Resistance

P
TJMax-TA TJMaxTA
D MAX = 0 JC + OCA or---o:;;;:OCA = OCS

><
><

= Junction Temperature

+ PD (OJC + OcAl or
+ PDOJA (without heat sink)
High Stability 1 Amp Regulator
-

.....- -....--~----~-~""'""------~.....-VOUT (+)

.----+----,,?
+
=;II'F
C3

r.~Dl
.~ .. Lt.t320

200pF:;::

71;-3

=~Cltt

-':'2.2I'F

I..,/+f=-<

Ql
2N4093

7V

R2·

LJ
sVLt.t308
..
'1+-·-....
...,5<
-I'

..~C2tt

;;;'= IO I'F

4 ~~2'-1--_ _•
R5
10k

GND

I

LM790S

II

R3·

--------~...;;;+--

.,O:..U.,.T...- -...

VOUT (-)
TL/H/7340-5

Load and line regulation

< 0.Q1 % temperature stability

,;; 0.2%

tDetermine Zener current
ttSolid tantalum
'Select resistors to set output voltage. 2 ppm/'C tracking suggested

1-223

Typical Applications (Continued)
Current Source

-~I\.
2.21'F

I
I

+

_.

SOLID
TANTALUM

INPUT
'lOUT

= 1 mA + ~
Ai

D.lI'F

I

OUT

OUTPUT
TL/H/7340-7

Light Controller Using Silicon Photo Cell
I
I
I
I

5V- 15V
BULB

Cit ..J!
2511FT

USA
MAX TURN-ON
CURRENT

I
I
I
I

TLlH17340-8

'Lamp brightness Increase until II = la ('" 1 mAl + SVlAI.
tNecessary only Hraw supply filter capacitor Is more than 2' from LM7905CT

1-224

r-----------------------------------------------------------------------------, r
.....
==
CD

Typical Applications (Continued)

><
><

High-Sensitivity Light Controller
I
I
I
I

8Y - ISY
BULB

CIt ....I!.
2S}'f '"T"
I
I
I
I

1.7SA

MAX TURN-ON
CURRENT

TLIH/7340-9

'Lamp brightness Increases until il

= 5V1Rl

(II can be sel as low as 1 pA)

tNecessary only If raw supply filler capacilor Is more Ihan 2" Irom LM790S

± 15V, 1 Amp Tracking Regulators
+YIN

o-...--~IN~

~O;.;;U~T......- - - - -...- - -...- -..._o

VOUT (+) 15V

R4·
10k

1%

...!!.

01

RS·

C4··
2S}'fT

6

lN4001

10k

1%

I
I
I
I

....- - - - -....- .....- - + - - - - - - -....-+--+-0
CS··
2S}'f

...!!.
T
I
I
I

-YIN

COMMON

02

lN4001

0-+---"""

.."."",.........- - - - - - - -.....---4....a YOUT (-)

ISY
TLIH/7340-1

Load Regulation at AIL = lA
Oulput Ripple, GIN = 3000 I'F, IL = lA
Temperature Stability
Output Noise 10 Hz ,; 1 ,; 10 kHz

(-15)
40mV
IOOI'Vrms
50mV
150I'Vrms

(+15)
2mV
IOOI'Vrms
50mV
150l'Vrms

'Resistor tolerance 01 R4 and R5 determine matching 01 (+) and (-)
outputs.
• 'Necessary only if raw supply filter capacitors are more than 3" from regulators.

1-225

II

LM79XX

en
n

:z
CD

-n"
3

I»

-5V

c

i"

':"

RI8
4k

01

~

-& 02

R6
lk

R5
15k

06

~

.;,

I\)

I I

m

t t:i r

"r
:" j

I

R4

•• 0

I I~

[
_

RB
20k

r

R9
20k

)

[

! ...

5k

I»

3

5k

" ~ d'" t
w.,ii n
~

...

co

:'.~
L fi·k-l I
150

(II

0'_
03
6.2V

~R16
0.2
TL/HI7340-12

en
()
::J'
CD

3m

-8V, -12Vand -15V

5"

c

i"
Dl

':"

RI8

RIg

4k

5k

cc
3

(I)

'0
o
:J

§'
c:
m

B

R17

~

""

"1

1,

(n

J r

OVOUT

03
6.2V

20 pF
R4
20k
R3
6k

V,NO

1 11 1 1 1 1

R8
20k

R9
20k

11

OK

50

~

R16
0.2

TUH17340-13

XX6lW1

II

Section 2
Low Dropout
Voltage Regulators

Section 2 Contents
Low Dropout Voltage Regulators-Definition of Terms ..................................
Low Dropout Regulators-Selection Guide ............................................
LM330 3-Terminal Positive Regulator... ..... .... ........................ .............
LM2925 Low Dropout Regulator with Delayed Reset . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM29261 LM2927 Low Dropout Regulators with Delayed Reset. . . . . . . . . . . . . . . . . . . . . . . . . . .
LM2930 3-Terminal Positive Regulator.. ..... ...... .......... .......... ... ......... ...
LM2931 Series Low Dropout Regulators. . . . . . . . . .. . . . . . . . . . . . . .. . . . . . . . . .. . . . . . . . . . . . .
LM2935 Low Dropout Dual Regulator .......... . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM2936 Ultra-Low Quiescent Current 5V Regulator. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM2937 500 rnA Low Dropout Regulator ..............................................
LM2940/LM2940C 1A Low Dropout Regulators...................... ... .. ....... .. ....
LM2941 ILM2941 C 1A Low Dropout Adjustable Regulators ..............................
LM2984 Microprocessor Power Supply System. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM2990 Negative Low Dropout Regulator ..........•..................................
LM2991 Negative Low Dropout Adjustable Regulator ...................................
LP2950/LP2950AC/LP2950C 5V and LP2951 ILP2951 AC/LP2951 C Adjustable Micropower
Voltage Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LP2952/LP2952A1LP2953/LP2953A Adjustable Micropower Low-Dropout Voltage
Regulators .................................................•....................
LP2954/LP2954A 5V Micropower Low-Dropout Voltage Regulators. . . . . . . . . . . . . . . . . . . . . . .

2-2

2-3
2-4
2-6
2-10
2-16
2-24
2-29
2-36
2-44
2-49
2-54
2-63
2-69
2-82
2-89
2-95
2-108
2-121

~

~National

c

a

~ Semiconductor

""D

o
C

Low-Dropout Voltage Regulators
Definition of Terms

~

iif
co
CD

:::u
CD

co

c

Dropout Voltage: The input-voltage differential at which
the circuit ceases to regulate against further reduction in
input voltage. Measured when the output voltage has
dropped 100 mV from the nominal value obtained at (VOUT
+ 5V) input, dropout voltage is dependent upon load current and junction temperature.

Load Regulation: The change in output voltage for a
change in load current at constant chip temperature.
Long Term Stability: Output voltage stability under accelerated life-test conditions after 1000 hours with maximum
rated voltage and junction temperature.

Input Voltage: The DC voltage applied to the input terminals with respect to ground.

Output Noise Voltage: The rms AC voltage at the output,
with constant load and no input ripple, measured over a
specified frequency range.

Input-Output Differential: The voltage difference between
the unregulated input voltage and the regulated output voltage for which the regulator will operate.

Quiescent Current: That part of the positive input current
that does not contribute to the positive load current. The
regulator ground lead current.

Line Regulation: The change in output voltage for a
change in the input voltage. The measurement is made under conditions of low dissipation or by using pulse techniques such that the average chip temperature is not significantly affected.

Ripple Rejection: The ratio of the peak-to-peak input ripple
voltage to the peak-to-peak output ripple voltage.

ao
Cil
C

CD

::::!':
:J

::;:

o·
:J

-...
o

~

3
(II

Temperature Stability of VO: The percentage change in
output voltage for a thermal variation from room temperature to either temperature extreme.

PI

2-3

Low Dropout Regulators Selection Guide

~
feZ

Low Dropout Regulators Selection Guide
output
CUrrent

Device

(A)
1.0

LM2940
LM2940C
LM2941

0.75

0.5

0.25

--

Dropout
Voltage

(V)

(V)

Typical
Maximum
Reverse
Quiescent
Input
Polarity
Voltage
Current
Protection
(mA)
(V)
(V)

5,8,12,15

1.0'

26

10

-15

5,8,9,10,12

1.0'

26

10

-15

Transient
Protection
(V)

+60"/-50
+60"/-50

Operating
Package
Temperature
Availabilityt
(TJOC)

Page
No.

-55 to +150

K2:j:

2-54

-40 to +150

T3

2·54

5,12,15

1.0'

26

10

-15

+45/-45

Oto +150

T3

2·54

Adj. (5 to 20)

1.0'

26

10

-15

+60"/-50

-55 to +150

K4:j:

2-63

Adj. (5 to 20)

1.0'

26

10

-15

+60"/-50

-40 to +150

T5

2·63

-15

+45"/-45

Adj. (5 to 20)

1.0'

26

10

Oto +150

T5

2·63

LM2990

-5, -5.2, -12, -15

1.0'

-26

1

-40 to +125

T3

2-82

LM2991

Adj. (-2to -25)

1.0'

-26

0.7

-40 to +125

T5

2-89

LM2925

5

0.82

26

3

-15

+60"/-50

-40 to +150

T5

2-10

LM2935

Two 5V Outputs

0.82

26

3

-15

+60"/-50

-40 to +150

T5

2-36

LM2926

5

0.7'

26

2

-18

+80"/-50

-40 to +125

T5

2-16

LM2927

5

0.7"

26

2

-18

+80"/-50

-40 to +125

T5

2-16

LM2937

5,8,10,12,15

1.0'

26

2

-15

+60"/-50

-40 to +125

T3

2-49

LM2984

Three 5V Outputs

1.1*

26

14

-15

+60"/-35

-40 to +150

T11

2-69

LP29521

5, Adj. (1.23 to 29)

O.S·

30

0.130

-20

-40 to +125

M16, N14

2-1 OS

LP2952A1

5, Adj. (1.23 to 29)

0.8"

30

0.130

-20

-40 to +125

M16, N14

2-108

LP29531

5, Adj. (1.23 to 29)

0.8'

30

0.130

-20

-40 to +125

M16, N16

2-1 OS

LP2953AI

5, Adj. (1.23 to 29)

O.S"

30

0.130

-20

-40 to +125

M16,N16

2-1 OS

LP2953AM

LM2941C

~

output
Voltage

5, Adj. (1.23 to 29)

O.S·

30

0.130

-20

-55 to +125

J16:j:

2-1 OS

LP29541

5

0.8'

30

0.090

-20

-40 to +125

T3

2-121

LP2954AI
-

5

0.8'

30

0.090

-20

-40 to +125

T3

2-121

2.m
::::10

ga.
~J

~m

""-

Low Dropout Regulators Selection Guide (Conlinued)
Output
Current
(A)

0.15

0.1

Maximum
Input
Voltage
(V)

Typical
Quiescent
Current
(mA)

Reverse
Polarity
Protection
(V)

Transient
Protection
(V)

Operating
Temperature
(TlC)

0.6

26

3.5

-12

+50/-30

010 +125

T3

2-6

5,8

0.6

26

4

-6

+40·'/-12

-4010 +125

T3

2-24

5

0.6

24

Q.400

-15

+60"/-50

-4010 +125

M8, T3,Z3

2-29

LM2931C

Adj. (3 10 29)

0.6

24

Q.400

-15

+60.°/-50

-4010 +125

M8,T5

2-29

LP2950C

5

0.6·

30

0.075

-4010 +125

Z3

2-95

Output
Voltage
(V)

Dropout
Voltage

LM330

5

LM2930
LM2931

Device

01

0.05

Page
No.

5

0.6·

30

0.075

-4010 +125

Z3

2-95

LP2951

5V Adj. (l.24V 10 29)

0.6'

30

0.075

-5510 +150

H8, J8, E20:j:

2-95

LP2951C

5V Adj. (1.24V 10 29)

0.6'

30

0.075

-4010 +125

M8,N8

2-95

LP2951AC

5V Adj. (1.24V 10 29)

0.6'

30

0.075

-4010 +125

M8,N8

2-95

-4010 +125

M8,Z3

2-44

LP2950AC
I}'

(V)

Package
Availability1'

LP2936

5

0.4

40

0.009

-15

+60/-50

·Guaranteed maximum dropout voltage at full load over temperature.
"''''Positive transient protection value also indicates the regulator's load dump capability.
tunder Package Availability the letter identifies the type of package available and the number indicates the number of leads of the indicated package.
For example: T5 ~ 5-Lead TO-220. and M8 ~ 8-Lead Surface Mount.

E: Leadless Ceramic Chip Carrier
H: Metal Can (TO-99)
J: Ceramic Dual-In-Une Package
K: Metal Can (TO-3)
M: Small Outline Molded Package (Surface Mount)
N: Molded Dual-In-Line Package
T: TO-220
Z: TO-92
*Available in indicated package only as a military specified device.

ap!n9 UO!I:»alas SJOleln6al::llnodoJC MOl

II

~

~ ~Nattonal

~ Semiconductor

LM330 3·Terminal Positive Regulator
General Description

Features

The LM330 5V 3-terminal positive voltage regulator features
an ability to source 150 mA of output current with an inputoutput differential of 0.6V or less. Familiar regulator features
such as current limit and thermal overload protection are
also provided.
The low dropout voltage makes the LM330 useful for certain
battery applications since this feature allows a longer battery discharge before the output falls out of regulation. For
example, a battery supplying the regulator input voltage may
discharge to 5.6V and still properly regulate the system and
load voltage. Supporting this feature, the LM330 protects
both itself and regulated systems from negative voltage inputs resulting from reverse installations of batteries.

•
•
•
•
•
•
•
•

Input-output differential less than 0.6V
Output current of 150 mA
Reverse battery protection
Line transient protection
Internal short circuit current limit
Internal thermal overload protection
Mirror-image insertion protection
P+ Product Enhancement tested

Other protection features include line transient protection
up to 26V, when the output actually shuts down to avoid
damaging internal and external circuits. Also, the LM330
regulator cannot be harmed by a temporary mirror-image
insertion.

Schematic and Connection Diagrams
IN

GND
TUH/930B-1

(TO-220)
Plastic Package

TL/H/930B-2

Front View
Order Number LM330T-S.0
See NS Package Number T03B

2-6

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Operating Range
26V
Line Transient Protection (1000 ms)
40V

Internal Power Dissipation
Operating Temperature Range

Internally Limited
O'Cto +70'C

Maximum Junction Temperature

+ 125'C

Storage Temperature Range
Lead Temperature (Soldering, 10 sec.)

- 65'C to + 150'C
+300'C

Electrical Characteristics (Note 1)
Symbol
Vo

I:,vo

Parameter

Conditions

Output Voltage

Tj = 25'C

Output Voltage
Over Temp

5
6

Line Regulation

9 < Y,N < 16V, 10 = 5 mA
6 < Y,N < 26V, 10 = 5 mA

Load Regulation

5

< 10 < 150mA
< Y,N < 26V; O'C :;;; Tj :;;; 100'C

Min

Typ

Max

4.6

5

5.2
V

4.75

< 10 < 150mA

Long Term Stability
10

5.25
7
30

25
60

14

50

20

Quiescent Current

'0=10mA
= 50mA
10 = 150mA

3.5
5
18

Line Transient
Reverse Polarity

Y,N = 40V, RL = 100n,1s

14
-80

~Io

Quiescent Current
Change

Y,N

Overvoltage Shutdown
Voltage

'0

V,N = -6V, RL = 1000

6

< Y,N < 26V
26

mV

mV/1000 hrs
7
11
40

mA

%

10

Max Line Transient

38
60

1s, Vo:;;; 5.5V
Reverse Polarity
Input Voltage

Units

V

50
-30

DCVo

>-

0.3V, RL = 100n

Output Noise Voltage

10 Hz-100 kHz

Output Impedance

10 = 100 mADC + 10 mArms

-12

Ripple Rejection

50

}J-V

200

mn

56

Current Limit

150

Dropout Voltage

10 = 150mA

Thermal Resistance

Junction to Case
Junction to Ambient

dB

400

700

mA

0.32

0.6

V

4
50

'C/W

Note 1: Unless otherwise specified: VIN = 14V, 10 = 150 rnA. Tj = 25'C, Cl = 0.1 /!F, C2 = 10 /!F. All characteristics except noisevollage and ripple rejection
are measured using pulse techniques (tw ,; 10 ms, duty cycle,; 5%). Output voltage changes due to changes in internal temperature must be taken into account
separately.

2-7

Typical Performance Characteristics
Dropout Voltage

Dropout Voltage
0.6

8
~.

~

is

Low Voltage Behavior
6.0

0.6

0.5
0.4
0.3 ~

5

I!:
::> 0.2
0

5... 0.1 V
2!;

o

~

o

...-

-

25

8

-

50

~
1o=lr° rnA

~
~

TJ=250 C
0.5

8

0.4

~

!:i

0.3

0

I!:
::> 0.2
0

,!.

...
::>

75

100

125

,/

0.1

o

o

150

5

5

,/

0

,I'

2!;

10= OmA

>

... V

5

1o=~OrnA

50

JUNCTION TEMPERATURE (OC)

1o=150mA

5.5

100

150

s.o
4.5

4.0

/

3.5
3.0

/

2.5
2.0
1.5
1.0

J
INPUT VOLTAGE (V)

Line Transient Response
TJ=25OC
1o=150mA

u.t330T-5.0
RL = 1000

1\

Load Transient Response

C~tj,l~~F

C2=10j.lF

'I,

"'"

!/

s.o 5.5 6.0 6.5

1.5 2.0 2.5 3.0 3.5 4.0 4.5

200

OUTPUT CURRENT (rnA)

High Voltage Behavior

/

/

.\

r

t....

"-

1\

I
I

II
o

o

o

10 15 20 25 30 35 40

TIME (1'.)

Peak Output Current

Quiescent Current

600

35

TJJ50 C

~ ~.

~aoc

V
I

TJ= 125°C

~

:c-S.

i

10

30

20

25

u

~

20

,/

ffi

15

gj
a

10

......

I-""
o
o

30

INPUT VOLTAGE (V)

!

is

0:
0:

B

IS

~

a

TJ=250C

70
;Q

50

:2z:

iil

10= 150 rnA

~

10

~

0:

10=OrnA 10-50mA

10

20

INPUT VOLTAGE (V)

~

!Z

"

gj

"

10=0

a

o
30

60

90

120

-60 -40

150

30

40

80

120

160

Ripple Rejection

10=50rnA

,

60
50

e;;- 60
:2z:

0

i'\. /

§

"

30

;J

40

0:

~

il1

20

10

0

JUNCTION TEMPERATURE (OC)

60

1\IN=14V

0
1

~

10=50 rnA

~

20
VIN -VOur =9V
'o=120Hz

10

0
0

16

B
::>

E 40

40

20

10= 150 rnA

18

Ripple Rejection
60

60

30

0:

VIN = 14V

20

OUTPUT CURRENT (mA)

Quiescent Current
70

!

25

::>

u

15

Quiescent Current
22

VIN = 14V
TJ=250 C

::>

o
o

30

15

INPUT VOLTAGE (V)

100

lk

10k lOOk

FREQUENCY (Hz)

2-8

111

o

o

50

100

150

OUTPUT CURRENT (mA)
TUH/9306-3

Typical Performance Characteristics
Output Impedance
10

I
~

Overvoltage Supply Current
RL = loon
25 T)=25OC

1

r-..

1

~

0

;'

o.1

~

:>

15

~

10

I
10

I

I

100

lK

I

20

o.z

If
V
i"'"

~

~!i!
0

-4

-200
-12 -10

40

35

-6

-4

-2

Output Voltage (Normalized
to 5V atT, = 25'C)
5.025

.J

V'N= 14V

~

0.15

i'..

I\.

0.1

0.05

o """"

-2

-s

INPUT VOLTAGE (V)

RL=CO
T)=25OC

5

1';

-a -a

,/
/'

Output at Overvoltage

0.
1 RL=CO.J
T)=25OC

-12 -10

-150

INPUT VOLTAGE (v)

Output at Reverse Supply

-0.3

-100

~

V

-250

FREQUENCY (Hz)

1

-50

i0

~

./

o

1~

10K lOOK

i-"""

T)=25OC

[/1'

1

20

iil

0

0.0 1
1

Reverse Supply Current
50

30

'0=50mA
T/=25OC

g
tl

(Continued)

I-

30

INPUT VOLTAGE (V)

i ~925

-

4.900

-60-40-20 0 20 40 60 80 100120140

40

35

INPUT VOLTAGE (V)

JUNcnON TEMPERATURE (OC)
TLIH/9306-4

Typical Applications
The LM330 Is designed specifically to operate at lower Input
to output voltages. The device is designed utilizing a power
lateral PNP transistor which reduces dropout voltage from
2.0V to O.3V when compared to IC regulators using NPN
pass transistors. Since the LM330 can operate at a much
lower input voltage, the device power dissipation Is reduced,
heat sinking can be simpler and device reliability 1m-

proved through lower chip operating temperature. Also, a
cost savings can be utilized through use of lower powerl
voltage components. In applications utilizing battery power,
the LM330 allows the battery voltage to drop to within O.3V
of output voltage prior to the voltage regulator dropping out
of regulation.

50

YIN
UNREGULATED
INPUT

Cl·

O.I~FI

YOUT
REGULATED
+ C2··OUTPUT

40

g

Il0~F

Ell 30

~

TL/H/930s-6

e.=i

~

• Required If regulator Is located far from power supply filter.
.. C2 may be either an Aluminum or Tantalum type capacitor but
musl be raled 10 operale at - 40'C to guarantee regulator stablilly
to Ihat temperature extreme. 10 f'F Is the minimum value required
for stability and may be Increased without bound. Locate as close
as possible to the regulaHon.

J

v

...........

I

"-

~

\

20
10

o
o

25

50

75

100

125

150

'OUT (mA)
TL/H/930e-e

Note: Compared to IC regulator with 2.DV dropout voltage and
10m••• = 6.0 mAo

2-9

~National
~ semiconductor

LM2925 Low Dropout Regulator with Delayed Reset
General Description

Features

The LM2925 features a low dropout, high current regulator.
Also included on-chip is a reset function with an externally
set delay time. Upon power up, or after the detection of any
error in the regulated output, the reset pin remains in the
active low state for the duration of the delay. Types of errors
detected include any that cause the output to become
unregulated: low input voltage, thermal shutdown, short circuit, input transients, etc. No external pull-up resistor is neeessBJy. The current charging the delay capacitor is very low,
allowing long delay times.

•
•
•
•
•
•
•
•
•
•
•

Designed primarily for automotive applications, the LM2925
and all regulated circuitry are protected from reverse battery
installations or two-battery jumps. During line transients,
such as a load dump (60V) when the input voltage to the
regulator can momentarily exceed the specified maximum
operating voltage, the 0.75A regulator will automatically
shut down to protect both internal circuits and the load. The
LM2925 cannot be harmed by temporary mirror-image insertion. Familiar regulator features such as short circuit and
thermal overload protection are also provided.

5V, 750 mA output
Externally set delay for reset
Input-output differential less than 0.6V at 0.5A
Reverse battery protection
60V load dump protection
- 50V reverse transient protection
Short circuit protection
Internal thermal overload protection
Available in plastic TO-220
Long delay times available
P+ Product Enhancement tested

Typical Application Circuit
Vi
-!-Cl*

*l~F

11
INPUT
OUTPUT
VOLTAGE VOLTAGE

q'
Your 5V
750mA

+

C2**

~10~F
RES~.....!! RESET
FLAG

'Required if regulator is located far from
power supply filter.

LM2925

GNO

1
3

"CoUT must be at least 10 f'F to maintain
stability. May be increased without bound
to maintain regulation during transients.
Locate as close as possible to the regula·
tor. This capacitor must be rated over the

~ELAY
~C3

0.1

same operating temperature range as the
regulator. The equivalent series resist·

~F

~

ance (ESR) of this capaCitor is critical;

see curve.
TUH/526B-l

FIGURE 1. Test and Application Circuit

Connection Diagram
TO-220 5-Lead

~"""-

4 DELAY
3 GROUND
2 OUTPUT VOLTAGE (Vour)
1 INPUT VOLTAGE (VIN)

FRONT VIEW

TL/H/526B-2

Order Number LM2925T
See NS Package Number T05A
2-10

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Operating Range
Overvoltage Protection

Operating Temperature Range

150'C

Storage Temperature Range

-65'Cto + 150'C

Lead Temperature
(Soldering. 10 seconds)

26V
60V

Internal Power Dissipation (Note 1)

-40'Cto + 125'C

Maximum Junction Temperature

260'C

ESD rating is to be determined

Internally Limited

Electrical Characteristics for VOUT
VIN = 14V, C2 = 10 ",f, 10 = 500 mA, TJ = 25'C (Note 3) (unless otherwise specified)
Parameter

Typ

Min

Conditions

Max

Units

Note 2
Output Voltage
6V~ VIN ~ 26V, 10 ~ 500
-40'C~ TJ ~ +125'C

mA,

Line Regulation

9V ~ VIN ~ 16V, 10 = 5 mA
6V ~ VIN ~ 26V, 10 = 5 mA
~

~

V
4.75

5.00

5.25

4
10

25
50

10

50

mV
mV

Load Regulation

5mA

Output Impedance

500 mADC and 10 mArms,
100 Hz-10 kHz

200

Quiescent Current

10 ~ 10mA
10 = 500mA
10 = 750mA

3
40
90

10 Hz-100 kHz

100

",Vrms

20

mV/1000 hr

Output Noise Voltage

10

500mA

Long Term Stability
fo=120Hz

66

Dropout Voltage

10= 500mA
10 = 750mA

0.45
0.82

Maximum Operational
Input Voltage
Maximum Line Transient

Va ~ 5.5V

Reverse Polarity Input
Voltage, DC

Va;:" - 0.6V, 100 Load

Reverse Polarity Input
Voltage, Transient

1 % Duty Cycle,
100 Load

T ~

100 ms,

mA
mA
mA

100

Ripple Rejection

Current Limit

mV
mO

dB
0.6

V
V

0.75

1.2

A

26

31

V

60

70

V

-15

-30

V

-50

-80

V

Electrical Characteristics for Reset Output
VIN = 14V, C3 = 0.1 ",F, TA = 25'C (Note 3) (unless otherwise specified)
Parameter

Min

Conditions

Typ

Max

Units

Note 2
Reset Voltage
Output Low
Output High

ISINK = 1.6 mA, VIN = 35V
ISOURCE = 0

4.5

Reset Internal Pull-up Resistor
Reset Output Current Limit

VRESET = 1.2 V

VOUT Threshold
Delay Time

Ca = .005",F
Ca = 0.1 ",F
Ca = 4.7 ",F tantalum

150

0.3
5.0

0.6
5.5

V
V

30

kO

5

mA

4.5

V

12
250
12

ms
ms
s

300

2.5
Delay Current
Pin4
1.2
1.95
",A
Note 1: Thermal resistance without a heat sink for iunction to case temperature is 3'C/W (TO-220). Thermal resistance for TO-220 case to ambient temperature Is
50·C/W.
Note 2: These parameters are guaranteed and 100% production tested.
Note 3: To ensure constant junction temperature. low duty cycle pulse testing is used.

2·11

•

l:Q
~

:5

Typical Circuit Waveforms
60V

INPUT
14V

VOL~~G~ 14V
IV)

OV
5Y

OUTPUT
VOLTAGE
PIN 2

IV)

OV

RESET
VOLTAGE
PIN 5

IV)

oV

SYSTEM
CONDITION

I

TURN
ON

LOAD
DUMP

I

UNE NOISE, ETC.

LOWVIN

I

VOUT
SHORT
CIRCUIT

THERMAL
SHUTDOWN

TURN
OFF
TLfHf52BB-3

FIGURE 2

Typical Performance Characteristics
Reset Voltage

Delay Time

Reset Voltage

6

2.4

>

LOW-

Ift=I.6 mA

-40

i

1.6

~

1.2

i

-

-

I

o

lOt

2.0

HIGH
18=0

r-- r--

10·

_.....VJ

o.B
0.0

4U
BO
120 180
JUNCTION TEMPERATURE I'C)

..

o

2
4
INPUT VOLTAOE IV)

Reset Pull-up
Resistor R10

C3=0.1 ~F

..........

,/

..... ioooo

)~

TLfHf52BB-8

50

J

V

,

TLfHfS266-S

22D

d=o I
-10=600 mA

10

~

0.1
10- 4 10- 3 10- 2 10- 1 1 10 100
DELAY CAPACITOR I~F)

o

Delay Time

6

,,

103

~ 100

RESET CURRENT (mAl

Reset Voltage
on Power-up

/

!

~

10 4

0.4

TLfHf526B-4

o/

!

180
-40

r'-.

0
40
eo 120 110
JUNCTION TEMPERATURE ('C)

TLfHf5266-7

TLfHfS266-8

2·12

i

40

IIi!

3D

./

v

~~

V

20
-4U

0
4U
10 120 160
JUNCTION TEMPERATURE I'C)
TLfHfS28B-9

Typical Performance Characteristics
Dropout Voltage

!5

w_

~1i
!:i-

DB

~i!i

D.6
'our= 500 mA
Q.4

-10

w
co_

-20

~~

..

0.2

~

0

>'"
....
:!f

-.co

.co

0

~c,:,

80

120

70

'"

~

~

i!l 60

1---_

§

~

UI

'"

50

~
0;

3
2
1
0

"':c

'our=IOO mA

'--- II

0

~~
.... ill
6'"

10 =120 Hz

11\

10

"'w

0
I

80

20

~

5

Ripple Rejection

Line Transient Response

1.0

I

(Continued)

40
30

10

0

160

20

3D

40

50

0

60

150
300 450 600
OUTPUT CURRENT (mAl

TIME (,..1

JUNCTION 1[MPERATURE (ae)

750

TUH/5268-12

TUH/5268-11

TUH/5268-10

Ripple Rejection

Quiescent Current

so

'"
1:!.

70

~UI

60

111111

'"

~

r;

5

'"
'"
'"

60

~

40

a

20

~

40

10k

lk
100
FREQUENCY (Hz)

w

RL=IOG

4

~

3

....

2

'"

1
0

~

~

0

~

-1

oV

30
10

"./

V

~

1/

/

I.)

8:
0;

1

so

iii

VuUT
lOUT =500 rnA
C2=10pf

50

7
6

11111

z

Output Voltage

100

-2

150

300

600

450

OUTPUT CURRENT (mA)

TL/H/5268-13

60

20
40
-40 -20 0
INPUT VOLTAGE (V)

750

TUH/5268-15

TL/H/5268-14

-

Quiescent Current
50

1....
~

I.

30

IS

20

a

10

-

IOUT=~50 mA

0'"

~

J

lour = 500 mA
40

lOUT = 50 mA

0
-40

Quiescent Current

1....
~

40

120

lil=r

I.)

IS

50

a

25

~

1\loJT

160

-20

0

1.0

'"
!;
0

g

V

z

~
~

i

JI

0
0

5

10 15 20
25
INPUT VOIJAGE (VI

0

60

10

20 30 40
TlMEt'ls'

30

50

60

TUH/5268-18

Maximum Power
Dissipation (TQ-220)

.",

0.5

.co

20

I"-

TUH/5268-17

2

.'"....

.

1'-

INPUT VOLTAGE (V)

Peak Output Current

i'"

-150
g 0.8
"' .... 0.6
""z
"'w 0.4
.... :l1
'" 0.20

mA

lou~= olm~

-40

~

I

0

it !$ -50

,11

TL/H/5268-19

1.5

JoJ

~~

g ~-lDO

75

JUNCTION 1[NPERATURE (ae)

s

~> 100
~.s 50

mA

0

SO

150

! J.

100

'"
'"

I
0

Load Transient Response

125

22
20
18
16
14
12
10
8

Output Capacitor ESR

INFlNIIE HEAT SINK

I\.

S
lj
z

~

100

v

~

....

100C W HEAT SINK

&

~
-"",

AWBI£NT lEMPERATURE (OC)
TL/H/5268-21

2·13

i

II)

4
NO HEAT ~INK
2"0
0 10 20 30 40 50 80 70 80 90100

TL/H/5268-20

'"

§

CaUT = lOSOF

I>-..

V-'0 ~
10
V

STA~LE - ~--:
REGION

'~

/.

0.1

~

'"
S

0.01
0

100

200

300

400

500

OUTPUT CURRENT (mA)
TUH/5268-22

~

~

r---------------------------------------------------------------------------------,
Definition of Terms

Application Hints

Dropout Voltage: The input-output voltage differential at
which the circuit ceases to regulate against further reduction in input voltage. Measured when the output voltage has
dropped 100 mV from the nominal value obtained at 14V
Input, dropout voltage is dependent upon load current and
junction temperature.
Input Voltage: The DC voltage applied to the input terminals with respect to ground.

EXTERNAL CAPACITORS
The LM2925 output capaCitor is required for stability. Without it, the regulator output will oscillate, sometimes by many
volts. Though the 10 p.F shown Is the minimum recommended value, actual size and type may vary depending upon the
application load and temperature range. CapaCitor effective
series resistance (ESR) also effects the IC stability. Since
ESR varies from one brand to the next, some bench work
may be required to determine the minimum capaCitor value
to use in production. Worst-case is usually determined at
the minimum junction and ambient temperature and maximum load expected.
Output capacitors can be increased In size to any desired
value above the minimum. One possible purpose of this
would be to maintain the output voltages during brief conditions of negative input transients that might be characteristic of a particular system.

Input-Output Differential: The voltage difference between
the unregulated Input voltage and the regulated output voltage for which the regulator will operate.
Line Regulation: The change in output voltage for a
change in the input voltage. The measurement is made under conditions of low dissipation or by using pulse techniques such that the average chip temperature is not significantly affected.
Load Regulation: The change in output voltage for a
change in load current at constant chip temperature.
Long Term Stability: Output voltage stability under accelerated life-test conditions after 1000 hours with maximum
rated voltage and junction temperature.

Capacitors must also be rated at all ambient temperatures
expected in the system. Many aluminum type electrolytics
will freeze at temperatures less than -30·C, reducing their
effective capaCitance to zero. To maintain regulator stability
down to -40·C, capaCitors rated at that temperature (such
as tantalums) must be used.

Output Noise Voltage: The rms AC voltage at the output,
with constant load and no input ripple, measured over a
specified frequency range.
Quiescent Current: The part of the positive input current
that does not contribute to the positive load current. The
regulator ground lead current.
Ripple ReJection: The ratio of the peak-to-peak input ripple
voltage to the peak-to-peak output ripple voltage.

RESET OUTPUT
The range of values for the delay capacitor is limited only by
stray capacitances on the lower extreme and capaCitance
leakage on the other. Thus, delay times from microseconds
to seconds are possible. The low charging current, typically
2.0 microamps, allows the use of small, inexpensive disc
capacitors for the nominal range of 100 to 500 milliseconds.
This is the time required in many microprocessor systems
for the clock oscillator to stabilize when initially powered up.
The RESET output of the regulator will thus prevent erroneous data and/or timing functions to occur during this part of
operation. The same delay is incorporated after any other
fault condition in the regulator output is corrected.

Temperature Stability of Vo: The percentage change in
ouput voltage for a thermal variation from room temperature
to either temperature extreme.

2-14

Circuit Schematic
- >

~r_---+_-----~------4_------_+~

II
'-+-------+---+-_"'N~h

2·15

~ r-------------------------------------------------------------~------------_,

~
('\II
:E
....I

......
CD

('\II
G)
('\II

:E
....I

~National
~ semiconductor

LM2926/LM2927
Low Dropout Regulator with Delayed Reset
General Description
The LM2926 is a 5V, 500 mA, low dropout regulator with
delayed reset. The microprocessor reset flag is set low by
thermal shutdown, short circuits, overvoltage conditions,
dropout, and power-up. After the fault condition Is corrected,
the reset flag remains low for a delay time determined by
the delay capacitor. Hysteresis is included in the reset circuit to prevent oscillations, and a reset output is guaranteed
down to 3.2V supply input. A latching comparator is used to
discharge the delay capacitor, which guarantees a full reset
pulse even when triggered by a relatively short fault condition. A patented quiescent current reduction circuit drops
the ground pin current to 8 mA at full load when the inputoutput differential is 3V or more.

the L4947 and TLE4260 alternatives. The LM2926 is pinfor-pin compatible with the LM2925.

Features
•
•
•
•
•
•
•
•

Familiar PNP regulator features such as reverse battery protection, transient protection, and overvoltage shutdown are
included in the LM2926 making it suitable for use in automotive and battery operated equipment.

5% output accuracy over entire operating range
Dropout voltage typically 350 mV at 500 mA output
Externally programmed reset delay
Short circuit proof
Reverse battery proof
Thermally protected
LM2926 is pin-for-pin compatible with the LM2925
P+ Product Enhancement tested

Applications
• Battery operated equipment
• Microprocessor-based systems
• Portable instruments

The LM2927 is electrically identical to the LM2926 but has a
different pin-out. The LM2927 is pin-for-pin compatible with

Typical Application

Unregulated
Input

I VIN

'Required il regulator is located lar (> 2") Irom power supply filter.

"Co must be at least 10 ",F to maintain stability. May be Increased without
bound to maintain regulation during transients. Locate as close as possible
to the regulator. This capaCitor msut be rated over the same operating temperature range as the regulator. The equivalent series resistance (ESR) 01
this capaCitor is critical; see curve under Typical Performance CharacterIstics.

Delayed
Reset
Output

LM2926

t=---1P--Vo =5V. 500 rnA

TLfH110759-1

Connection Diagrams and Ordering Information

iiiiii

5-Lead To-220

Front View
Order Number LM2926T
See NS Package Number T05A

4 DELAY
CAPACITOR
5
DELAYED
RESET OUTPUT
3 GROUND
2 OUTPUT VOLTAGE (Vo)
1 INPUT VOLTAGE (VIN)
TLfH110759-2

5-Lead TO·220

Front View
Order Number LM2927T
See NS Package Number T05A

5 OUTPUT VOLTAGE (Vo)
4 DELAY CAPACITOR
3 GROUND
2 DELAYED RESET OUTPUT
1 INPUT VOLTAGE (VIN)
TUH110759-14

2-16

Absolute Maximum Ratings

(Note 1)
It Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Survival
t = 100 ms
80V
t = 1 ms
-50V
Continuous
-18Vto +26V
Reset Output Sink Current
10mA

ESD Susceptibility (Note 2)
Power Dissipation (Note 3)

2kV
Internally Limited
150'C

Junction Temperature (TJMAX)
Storage Temperature Range

- 40'C to + 150'C
260'C

Lead Temperature (Soldering, 10 sec.)

Operating Ratings

(Note 1)

Junction Temperature Range (TJ)
Maximum Input Voltage

-40'Cto + 125'C
26V

Electrical Characteristics VIN = 14.4V, Co = 10 ,...F, -40'C s: TJ s: 125'C, unless otherwise specified.
Parameter

Conditions

Typ
(Note 4)

Limit
(Note 5)

Units
(Limit)

4.85

V (min)
V
V (max)

REGULATOR OUTPUT
Output Voltage

5 mA s: 10
TJ = 25'C

s: 500 mA,
5

5.15
5 mA

s:

'0

s:

5.25

V (min)
V
V (max)

25

mV
mV(max)

50

mV
mV(max)

60

mV
mV(max)

3

mA
mA(max)

30

mA
mA(max)

10

mA
mA(max)

60

mA
mA(max)

200

mV
mV(max)

300

mV(max)

600

mV
mV(max)

700

mV(max)

800
3

mA(min)
A
A (max)

60

dB (min)

4.75

500 mA
5

Line Regulation

10
10

Load Regulation
Quiescent Current

10

10
10

Dropout Voltage (Note 6)

= 5 mA, 7V s: VIN s: 26V

5 mA

10
Quiescent Current at Low VIN

= 5 mA, 9V s: VIN s: 16V

10

s: 10 s:

500 mA

1
3
5

= 5mA

2

= 500mA

8

= 5mA, VIN = 5V

3

= 500 mA, VIN = 6V
= 5 mA, TJ = 25'C

25
60

= 5mA
10 = 500 mA, TJ = 25'C
10

350

= 500mA
VIN = 8V, RL = 10
10

Short Circuit Current

2
Ripple Rejection

fRIPPLE

= 120 Hz, VRIPPLE = 1 Vrms, 10 = 50 mA

= 50 mAdc and 10 mArms @ 1 kHz
= 50 mA

Output Impedance

10

Output Noise

10 Hzto 100 kHz, 10

mO

1

mVrms

20

Long Term Stability
Maximum Operational Input Voltage

100

mVll000 Hr
26

Continuous

2-17

V (min)

,.

Electrical Characteristics
VIN

=

14.4V, Co

=

10 p.F, -40"C

s:

s:

TJ

125·C, unless otherwise specified (Continued)

Parameter

Conditions

Typ
(Note 4)

Limit
(Note 5)

Units
(Limit)

REGULATOR OUTPUT (Continued)

s: 7V, RL =

Peak Transient Input Voltage

Va

Reverse DC Input Voltage

Va:? -0.6V, RL

Reverse Transient Input Voltage

t,

=

1 ms, RL

=

1000, t,

=

=

100 ms

1000

1000

BO

V (min)

-1B

V (min)

-50

V (min)

-80
-400

mV(min)
mV
mV(max)

0.4

V (max)

RESET OUTPUT
Threshold

AVO Required for Reset Condition (Note 7)
-250

Output low Voltage

IS INK

=

1.6 mA, VIN

=

3.2V

Internal Pull-Up Resistance

=

Delay TIme

CDELAY

Minimum Operational VIN
on Power Up

Delayed Reset Output s: 0.8V,
ISINK = 1.6 rnA, RL = 1000

Minimum Operational Vo
on Power Down

Delay Reset Output s: O.BV,
ISINK = 10 p.A, VIN = OV

10 nF (See Timing Curve)

0.15
30

kO

19

ms

2.2
3.2
0.7

V
V (rnin)
V

DELAY CAPACITOR PIN
Threshold Difference (AVDELAY)

Change in Delay Capacitor Voltage Required for
Reset Output to Return High

3.5
3.75
4.1
1.0

Charging Current (IDELAY)
2.0

3.0

V (rnin)
V
V (max)
p.A(rnin)
p.A
p.A (max)

Note 1: Absolute Maximum Ratings Indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional. but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrtcal Characteristics.
Note 2: Human bcdy model; 100 pF discharged through a 1.5 kO resistor.
Note 3: The maximum power dissipation is a function of TJMAX, and 9JA, and TA, and is limited by thennal shutdown. The maximum allowable power dissipation at
any ambienltemperature is Po = (TJMAX-TAl/9JA.1f this dissipation is exceeded, the die temperature will rise above 150"C and the device will go into thermal
shutdown. For the LM2926 and LM2927, the Junction·lo-amblentthennal resistance is 5~C/W, and the Juncllon-to·case thermal resistance is 3'C/W.
Note 4: Typlcals ara at TJ = 25'C and represent the most likely parametric nonn.
Note 5: Limits are 100% guaranteed by production testing.
Note 6: Dropout voltage Is the input-output differential at which the circun ceases to regulate against any further reduction in input voltage. Dropout voltage is
measured when the output voltage (Va) has dropped 100 mV from the nominal value measured at VIN = 14.4V.
Note 7: The reset flag is set LOW when the output voltage has dropped an amount, I1Vo, from the nominal value ineasured at VIN = 14.4V.

2-18

Typical Performance Characteristics
Output Voltage

Output at Voltage Extremes

Low Voltage Behavior

5.050

7r-~--'-~r--r--.--'

6

5.040
5.030

~

5.020

~

4.990

S

IL'5m~

5.010

/

5.000

~

I

/

4.980

.1

IL =500mA

V

:{

4.970

1/

4.960

-I L--'----'_.L.....L_L-.J
-40 -20
20
..0
60
80

4.950
-50 -25

0

2S

SO

7S

100

125

JUNCTION TEMPERATURE. TJ (\'C)

Supply Current
60

Quiescent Current
30

Rl = soon.

J

50

]:

~
i'l

~

/

40
30

I

A

20

25

i'l

IS

'L '

g

2Q

20

60

80

liJJ

Dropout Voltage

"
0

----- -

TC'2~

./

D.2

1£-

o
o

Te'

100

200

300

-tOOC
400

I~

500

Ripple Rejection
80
70

'"

60
50

o
o

~

~

~V

~V

r

T" 2 C

5

I

10

IS

20

Ripple Rejection

100

200

300

400

500

10 _ _ _

"~

INPUT VOLTAGE (v)

OUTPUT CURRENT (rnA)

90

~

1001!ll!~

TJ =25OJ

TC=125;'" ~

~

~

i1

....-::::

Output Capacitor ESR

I

0.6

0

T'-~

OUTPUT CURRENT (mA)

TJ I. -40J
J

~

0

T'250 C,

Output Current Limit

0.8

OA

10

o

RL -Ul.

g

ii'l

INPUT VOLTAGE (V)

1.0

~

!

i7r'J

012345678910

INPUT VOLTAGE (V)

E

Te~25~

/(/ TTr ~;;~

10

~

40

Quiescent Current
IS

A~t
~ r~!.1

o

-40 -20

r1

50 m

Tc=12SOC

!<

I(

o

1
~

/

V

10

INPUT VOLTAGE (v)

INPUT VOLTAGE (V)

25

30

1.0

O,'~~
O.OIEr
100
200
o

300

400

SOO

OUTPUT CURRENT (rnA)

Output Impedance

VIN"Ut~
=
10 =250mA

Co 10,uF'
ESR. 0.3n

40
30
20
10

o
100

Ik

10k

tOOk

1M
FREQUENCY (Hz)

FREQUENCY (Hz)

TUH/l0759-3

2-19

r-. ,---------------------------------------------------------------------------------,

C'II

en

C'II

:::&

Typical Performance Characteristics

(Continued)

..I

re
~

Line Transient Response

..I

22

Co= 10l'F

CO= 10l'F
1o=5oomA

:::&

Maximum Power
Dissipation (TO-nO)

Load Transient Response

INFINITE HEAT SINK

20

lB
16

I'-..

If

v
20

so

40

"

BO

TIME ClIo)

14
12
10

~

20

40

o

so

--

\

1 I.,...,

_

NO HEAT SINK

0

25

-r--....
so

75 100 125

AMBIENT ltMPERATURE, TA (OC)

Reset Delay

Reset Delay

10.0

40

30

~
~

.,...

...,..",1 J

-so -25

BO

TIWE ClIo)

3:

1\

1D"C/W HEAT SINK \

1.0

.....
20

Cd'~' =10nF

i'.

0.10
10

10

100

-so -25

1k

0

25

so

75 100 125

JUNCTION TEWPERATURE, TJ (OC)

DElAY CAPACITOR (nF)

TL/H/l0769-4

Typical Circuit Waveforms
BOV Load-dump Translenl

Inpul Vollage
Thonnal
Shutdown

Oolay CopacRo,
Vollage

OV
j--:':""-......J(
SV

Delayod Rosol
Output j-0:;.:V_ _--!
TUH/l0759-5

2-20

r-

is:

Applications Information
EXTERNAL CAPACITORS
The LM2926/7 output capacitor is required for stability.
Without it, the regulator output will oscillate at amplitudes as
high as several volts peak-to-peak at frequencies up to
500 kHz. Although 10 ,...F is the minimum recommended
value, the actual size and type may vary depending upon
the application load and temperature range. Capacitor
equivalent series resistance (ESR) also affects stability. The
region of stable operation is shown in the Typical Performance Characteristics (Output Capacitor ESR curve).
Output capacitors can be increased in size to any desired
value above 10 ,...F. One possible purpose of this would be
to maintain the output voltage during brief conditions of input transients that might be characteristic of a particular
system.
Capacitors must also be rated at all ambient temperatures
expected in the system. Many aluminum electroly1ics freeze
at temperatures below - 30·C, reducing their effective capacitance to zero. To maintain regulator stability down to
-40·C, capacitors rated at that temperature (such as tantalums) must be used.

As shown in Figure 1, the delayed reset output is pulled low
by an NPN transistor (02), and pulled high to Vo by an
internal 30 ko. resistor (R3) and PNP transistor (03). The
reset output will operate when Vo is sufficient to bias 02
(0.7V or more). At lower voltages the reset output will be in a
high impedance condition. Because of differences in the
VeE of 02 and 03 and the values of R1 and R2, 02 is
guaranteed by design to bias before 03, providing a smooth
transition from the high impedance state when Vo < 0.7V,
to the active low state when Vo > 0.7V.

Rl
50kll

Vo

~

External Pull-up
Resistor

R2
100kll
R3
-:.: 30kll

Delayed Reset Output
Q2
RESET

Ql

. --

DELAYED RESET
The delayed reset output is designed to hold a microprocessor in a reset state on system power-up for a programmable
time interval to allow the system clock and other powered
circuitry to stabilize. A full reset interval is also generated
whenever the output voltage falls out of regulation. The circuit is tripped whenever the output voltage of the regulator
is out of regulation by the Reset Threshold value. This can
be caused by low input voltages, over current conditions,
over-voltage shutdown, thermal shutdown, and by both
power-up and power-down sequences. When the reset circuit detects one of these conditions, the delay capacitor is
discharged by an SCR and held in a discharged state by a
saturated NPN switch. As long as the delay capacitor is held
low, the reset output is also held low. Because of the action
of the SCR, the reset output cannot glitch on noise or transient fault conditions. A full reset pulse is obtained for any
fault condition that trips the reset circuit.

-

TLIH110759-6

FIGURE 1. Delay Reset Output
The static reset characteristics are shown in Figure 2. This
shows the relationship between the input voltage, the regultor output and reset output. Plots are shown for various external pull-up resistors ranging in value from 3 ko. to an
open circuit. Any external pull-up resistance causes the reset output to follow the regulator output until 02 is biased
ON. COELAY has no effect on this characteristic.

When the output regains regulation, the SCR is switched off
and a small current (IOELAY = 2 ,...A) begins charging the
delay capacitor. When the capacitor voltage increases
3.75V (boVOELAY) from its discharged value,the reset output
is again set HIGH. The delay time is calculated by:
delay time = COELAyboVOELAY
IOELAY

TIME (j.s)

(1)

TLIH110759-7

FIGURE 2. Reset Output Behavior during Power-Up

or

Figure 2 is useful for determing reset performance at any
particular input voltage. Dynamic performance at power-up
will closely follow the characteristics illustrated in Figure 2,
except for the delay added by COELAY when Vo reaches 5V.

delay time :::: 1.9 X 106 COELAY
(2)
The constant, 1.9 X 106, has a ±20% tolerance from device to device. The total delay time error budget is the sum
of the 20% device tolerance and the tolerance of the external capacitor. For a 20% timing capacitor tolerance, the
worst case total timing variation would amount to ± 40%, or
a ratio of 2.33:1. In most applications the minimum expected
reset pulse is of interest. This occurs with minimum COELAY,
minimum boVOELAY, and maximum IOELAY. boVOELAY and
IOELAY are fully specified in the Electrical Characteristics.
Graphs showing the relationship between delay time and
both temperature and COELAY are shown in the Typical
Performance Characteristics.

The dynamic reset characteristics at power-down are illustrated by the curve shown in Figure 3. At time t = 0 the input
voltage is instantaneously brought to OV, leaving the output
powered by Co. As the voltage on Co decays (discharged
by a 1000. load reSistor), the reset output is held low. As Vo
drops below 0.7V, the reset rises up slightly should there be
any external pull-up resistance. With no external resistance,
the reset line stays low throughout the entire power down
cycle. If the input voltage does not fall instantaneously, the
reset signal will tend to follow the performance characteristics shown in Figure 2.
2-21

N
CD
N

en

.......
ris:
N
CD
N
~

Applications Information (Continued)
SYSTEM DESIGN CONSIDERATIONS
Many microprocessors are specified for operation at 5V
± 10%, although they often continue operating well outside
this range. Others, such as certain members of the COPS
family of microcontrollers, are specified for operation as low
as 2.4V.

I--

'"....~

§!
!:;

I!:
::>

9Y Battery

Delayed
Reset
Output

RL = 100A
Co =10pF
Cdelay =0

YIN

5

~
..,

Battery Powered Regulator with Flashing
LED for Low Battery Indication

Your

5Y!500 mA

LM2926/27

\

4

\

3

,\our

2

0

VRESET

~
Rr 3k

0

o

R=510k

•

8l\.......

LM3909

SOO 1000 1500 2000 2500 3000

TIt.lE (JLS)
TLIHl10759-8

FIGURE 3. Reset Output Behavior during Power-Down
Of particular concern is low voltage operation, which occurs
in battery operated systems when the battery reaches the
end of its discharge cycle. Under this condition, when the
supply voltage is outside the guaranteed operating range,
the clock may continue to run and the microprocessor will
attempt to execute instructions. If the supply voltage is outside the guaranteed operating range, the instructions may
not execute properly and a hardware reset such as is supplied by the LM 292617 may fail to bring the processor under control. The LM292617 reset output may be more efficiently employed in certain applications as a means of defeating memory WRITE lines, clocks, or external loads, rather than depending on unspecified microprocessor operating
conditions.
In critical applications the microprocessor reset input should
be fully characterized and guaranteed to operate until the
clock ceases oscillating.

TLlHl10759-9

General Microprocessor Configuration
+

YIN

Delayed
Reset
Output

INPUT TRANSIENTS

I---.

I~F ~
Your

5Y/500 mA

Lt.t2926/27

ADDRESS
BUS

The LM292617 are guaranteed to withstand positive input
transients to BOV followed by an exponential decay of
T = 20 ms (tf = 100 ms, or 5 time constants) while maintaining an output of less than 7V. The regulator remains
operational to 26 Voc, and shuts down if this value is exceeded.

TLIHl1 0759-1 0

2-22

Applications Information

(Continued)

Using the Reset to De-Activate Power Loads. The LM1921 is a Fully Protected 1 Amp High-Side Driver.
VIN

0--1----------1--+,1-------.
l~F

~

r----'--'--.
Delayed
Reset
Output

VOUT

5V/500 rnA

TUH110759-11

Generating an Active High Reset Signal

LM2926/27

Using the Reset to Ensure an Accurate Display
on Power-Up or Power-Down

~ph

t - -.....-1-o VOUT
Oelayed
Reset
Output

Reset

Vour

5V/500mA

LN2926/27

+

I

lk

TLIH110759-12

I

10PF

1PF

Reset
pP

..JJ..LIJJL

TLIH110759-13

2-23

•

~National

~ semiconductor

LM2930 3-Terminal Positive Regulator
General Description

Features

The LM2930 3-terminal positive regulator features an ability
to source ISO mA of output current with an input-output
differential of 0.6V or less. Efficient use of low input voltages
obtained, for example, from an automotive battery during
cold crank conditions, allows SV circuitry to be properly
powered with supply voltages as low as S.6V. Familiar regulator features such as current limit and thermal overload
protection are also provided.

•
•
•
•
•
•
•
•

Designed originally for automotive applications, the LM2930
and all regulated circuitry are protected from reverse battery
installations or 2 battery jumps. During line transients, such
as a load dump (40V) when the input voltage to the regulator can momentarily exceed the specified maximum operating voltage, the regulator will automatically shut down to
protect both internal circuits and the load. The LM2930 cannot be harmed by temporary mirror-image insertion.

Input-output differential less than 0.6V
Output current in excess of ISO mA
Reverse battery protection
40V load dump protection
Internal short circuit current limit
Internal thermal overload protection
Mirror-image insertion protection
P+ Product Enhancement tested

Voltage Range
LM2930T-S.0

sv

LM2930T-B.0

BV

Fixed outputs of SV and BV are available in the plastic TO220 power package.

Schematic and Connection Diagrams

(TO·220)
Plastic Package

FRONT VIEW
TL/H/5539-1

Order Number LM2930T-5.0 or LM2930T-S.0
See NS Package T038
2-24

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Operating Range
26V
Overvoltage Protection
40V
Reverse Voltage (100 ms)
-12V
Reverse Voltage (DC)
-6V

Internal Power Dissipation (Note 1)
Operating Temperature Range
Maximum Junction Temperature
Storage Temperature Range
Lead Temp. (Soldering, 10 seconds)

Internally Limited
-40'Cto +85'C
125'C
- 65'C to + 150'C
230'C

Electrical Characteristics (Note 2)
LM2930T·5.0 VIN= 14V, 10= 150 mA, TJ=25'C (Note 5), C2=10 ""F, unless otherwise specified
Parameter

Conditions

Typ

Output Voltage

Line Regulation
Load Regulation
Output Impedance
Quiescent Current
Output Noise Voltage
Long Term Stability
Ripple Rejection
Current Limit
Dropout Voltage
Output Voltage Under
Transient Conditions

5
6V:S:VIN:S:26V, 5 mA:S:lo:S:150 mA
-40'C:S:TJ:S:125'C
9V:S:VIN:S:16V, 10=5 mA
6V:S:VIN:S:26V, 10=5 mA
5 mA:S:lo:S:150 mA
100 mADe & 10 mArms, 100 Hz-10 kHz
10=10mA
10=150mA
10 Hz-100 kHz
fo=120Hz

10=150mA
-12V:S:VIN:S:40V, RL = 1000

Tested
Limit
(Note 3)
5.3
4.7

Design
Limit
(Note 4)

5.5
4.5
7
30
14
200
4
18
140
20
56
400
0.32

25
80
50
7
40

Unit
VMAX
VMIN
VMAX
VMIN
mVMAX
mVMAX
mVMAX
mil
mAMAX
mAMAX
""Vrms
mV/1000 hr
dB

700
150
0.6
5.5
-0.3

mAMAX
mAMIN
VMAX
VMAX
VMIN

Electrical Characteristics (Note 2)
LM2930T-S.0 (VIN = 14V, 10 = 150 mA, TJ = 25'C (Note 5), C2 = 10 ""F, unless otherwise specified)
Parameter

Conditions

Typ

Output Voltage

Line Regulation
Load Regulation
Output Impedance
Quiescent Current
Output Noise Voltage
Long Term Stability
Ripple Rejection
Current Limit
Dropout Voltage
Output Voltage Under
Transient Conditions

8
9.4V"VIN:S:26V, 5 mA:S:lo,,150 mA,
-40'C:S:TJ,,125'C
9.4V:S:VIN:S:16V, 10=5 mA
9.4V"VIN:S:26V, 10=5 mA
5 mA:S: 10:S: 150 mA
100 mADe & 10 mArms, 100 Hz-10 kHz
10=10mA
10=150mA
10Hz-100kHz
fo=120Hz

10=150mA

2-25

Design
Limit
(Note 4)

8.8
7.2
12
50
25
300
4
18
170
30
52
400
0.32

-12V"VIN:S:40V, RL =1000

Tested
Limit
(Note 3)
8.5
7.5

50
100
50
7
40

Unit
VMAX
VMIN
VMAX
VMIN
mVMAX
mVMAX
mVMAX
mO
mAMAX
mAMAX
""Vrms
mVl1000 hr
dB

700
150
0.6
8.8
-0.3

mAMAX
mAMIN
VMAX
VMAX
VMIN

•

Note 1: Thermal resistance wIIhout a heat sink lor junction to case temperature is 3'C/W and lor case to ambient temperature is 50'C/W.
Note 2: All characteristics are measured w~h a capaCitor acress the input of 0.1 ,.F and a capacitor across the output of 10 J.LF. All characteristics except noise
vollage and ripple rejection ratio are measured using pulse techniques (!w"; 10 ms, duty cycle,,; 5%). Output voltage changes due to changes in internal tempera·
ture must be taken into account separately.
Note 3: Guaranteed and 100% production tested.
Note 4: Guaranteed (but not 100% production tested) over the operating temperature and Input current ranges. These limits are not used to calculate outgoing
qual~ levels.
Note 5: To ensure conslant lunction temperature, low duty cycle pulse testing is used.
'Required Hregulator is located lar
from power supply Iilter.

Typical Application
LM2930
VIN
UNREGULATED
INPUT

1

VOUT
REGULATED
OUTPUT

+ C2**
IO

l'F
TlIH/5539-5

"CoUT must be atlesst 10 J.LF to
maintain stability. May be Increased without
bound to maintain regulation during
transients. locate as close as possible
to the regulator. This capacitor must be
rated over the same operating temperature
range as the regulator. The equivalent
series resislance (ESR) of this capacitor
should be less than 1n over the
expected operating temperature range.

Typical Performance Characteristics
Output Impedance
10

g

....
i"
.

Overvoltage Supply Current

..

Ir"o..

w

oS
I-

..8

c

I-

I!:

:5
0:

./

0.1

~

I:

ill·

50

C
oS

20

I-

:5
0:

15
10

./

10

100

Ik

10k

20

1M

lOOk

Output at Reverse

ill

25

35
30
INPUT VOLTAGE IV)

I
-iI.1

-iI.2

-~

>

~
HY-++++-HH-++;
"

..

~ 1.000

-I

-6

-4

-2

,..

!--t--:I;;-I-+-O;:l--t-+-+-1

......
~ 0.995 1-t--t-+-+++I"-..3oI.I\-+-i
~
ill 0.990 J-t--t-i-t-+-t-+-+-1

0.1

0.05

-10

1.005 r--r--,---r--.-r--r---r----r---,

~

0.15

..... ~
30

INPUT VOLTAGE (V)

V

Output Voltage (Normalized
to 1V at TJ = 25'C)

co

~"

'"

INPUT VOLTAGE IV)

~
~
w

L

/'~

-250
-12

40

2S'c+++-+-H-++;

I-

~

~ -150

0.2 r--r--r---.-..-...,--,---,r-o

RL . "
Tj'

/'

...g;>- -100

Output at Overvoltage

Supply 0.1 ,.....,.":"""'-,.....,.-'-"'-,.....,.-'--r-I
~

-50

-200

FREQUENCY 1Hz)

"

"'"

~

0
1

!i:

Tj=25'C

RL'I001!
Tj = 25'C

25

ill

0.01

.~

Reverse Supply Current

30

lo=·... mA
Tj' 25'C

ffi
cI 0.985 1-+-+-+-1-+-+-1-+-1

_

!:!

iI!C>
!-VIN = 14V
.. 0.990 L-.l-...L..~-L_L-.J-..J..-L.......I
-4U -20 0 20 40 60 80 100 120 140

I-+-+-+--II-+-;

35
INPUT VOLTAGE IV)

40

JUNCTION TEMPERATURE I'C)
TL/H/5539-4

2·26

Typical Performance Characteristics
Dropout Voltage

a
~

"ffi
~
c;

0.6

a
~

"

~

10.tmA r--

OA

~

0.3

I

loo5~mA

!;

"~

6.0

Tj=25°C

0.2

I-" ~

0.1

i!i

o

I

~

0.2

~i!i

IO=lOmA

~

0.3

....

0.1

50

100

150

V

/

o

V
50

100

150

!;

3.0

"

2.0

1/
L

2.0

3.0

4.0

5.0

6.0

INPUT VOLTAGE IVI

High Voltage Behavior

Line Transient Response
Tj o 2B'C
IO"'5DmA

I

'.0

200

OUTPUT CURRENT ImAI

RL" loon

V

4.0

~

JUNCTION TEMPERATURE I'CI

LMZ930·5

5.0

'""

~
>

",/

o

o

a...

OA

c;

LM2930·5
IO=150mA

0.5

;:

;:

~

Low Voltage Behavior

Dropout Voltage
0.6

I

0.5

(Continued)

Load Transient Response

V,N -VoUT" 9V
C2-10pF

...

~~
...

I
I
o

o

~

>z
""
...."':c"
!iu

10

20

30

40

15

INPUT VOLTAGE IVI

Peak Output Current

"....

I

400

"'"

~

r

300

~O'C
~.

".5....ffi

Tj""'Z5°C

,~ ~

200
100

o

~

20

§

15

13

10

;;;

15

20

25

30

o

Quiescent Current

40

....
ffi

30

~

~

20

"

10

c;

90

120

m

'""z

60

;;:

40

§

"' -;:ho

-40

~

ii:

'0" 5omA

0
40
80
120
JUNCTION TEMPERATURE reI

160

Ripple Rejection
80

~

m

""

...a:

'O"BOmA
-OmA

III
II

150

'O'SOmA
V,N - VOUT =9V

60

10UJ

'0"0

Ripple Rejection

60

a:

~

80
LM293o·5

"....ffi

rr- -

OUTPUT CURRENT ImAI

70

.5

I I I

16

"

60

30

Jo·,50mA

18

~

~I"""

INPUT VOLTAGE IVI

~

III

20

;;;

.......
o

10

a:

~~
",

"
o

".5....ffi

25

a:

45

"'.1

Quiescent Current
22

V,N = 14V
Tj=25'C

30

30
TIME

Quiescent Current

T.t5'C

500

....

~

15

45

35

600

.5

30
TIME '",I

'"l!i

60

...~

40

ii:

20

t;

'"" /

~

20

V,N-VoUT' 9V
'0=120 Hz

o

0
0

10

20

'NPUTVOLTAGE IVI

30

o
1

10

100

lk

10k

FREQUENCY IHzl

lOOk

1M

o

50

100

150

OUTPUT CURRENT ImAI
TL/H/5539-2

2-27

c~----------------------------------------------------------------------,

ii:::&
-'

Definition of Terms
Dropout Voltage: The input-output voltage differential at
which the circuit ceases to regulate against further reduction in Input voltage. Measured when the output voltage has
dropped 100 mV from the nominal value obtained at 14V
Input, dropout voltage is dependent upon load current and
junction temperature.
Input Voltage: The DC voltage applied to the Input terminals with respect to ground.
Input-output Differential: The voltage difference between
the unregulated Input voltage and the regulated output voltage for which the regulator will operate.
Line Regulation: The change In output voltage for a
change in the input voltage. The measurement is made under conditions of low dissipation or by using pulse techniques such that the average chip temperature Is not significantly affected.
Load Regulation: The change in output voltage for a
change in load current at constant chip temperature.

Long Term Stability: Output voltage stability under accelerated life-test conditions after 1000 hours with maximum
rated voltage and junction temperature.
Output Noise Voltage: The rms AC voltage at the output,
with constant load and no Input ripple, measured over a
specified frequency range.
Quiescent Current: That part of the positive input current
that does not contribute to the positive load current. The
regulator ground lead current.
Ripple ReJection: The ratio of the peak-to-peak input ripple
voltage to the peak-to-peak output ripple voltage.
Temperature Stability of Vo: The percentage change In
output voltage for a thermal variation from room temperature to either temperature extreme.

Maximum Power
Dissipation (T0·220)
22

INFINITE HEAT SINK

20
18

~

16
14
12
10

8
6

~

.....

I\.

T""- ,...,100c IW HEAT SINK
i'

4 INO HEAT JINK
2

o
o

l"-

l""'-"",

I I

10 20 30 40 50 60 70 80 90 100

AMBIENT TEMPERATURE (OC)

2-28

TLlH/5539-6

~National

~ Semiconductor

LM2931 Series Low Dropout Regulators
General Description

Features

The LM2931 positive voltage regulator features a very low
quiescent current of 1 mA or less when supplying 10 mA
loads. This unique characteristic and the extremely low input-output differential required for proper regulation (0.2V
for output currents of 10 mAl make the LM2931 the ideal
regulator for standby power systems. Applications include
memory standby circuits, CMOS and other low power processor power supplies as well as systems demanding as
much as 100 mA of output current.
Designed originally for automotive applications, the LM2931
and all regulated circuitry are protected from reverse battery
installations or 2 battery jumps. During line transients, such
as a load dump (60V) when the input voltage to the regulator can momentarily exceed the specified maximum operating voltage, the regulator will automatically shut down to
protect both internal circuits and the load. The LM2931 cannot be harmed by temporary mirror-image insertion. Familiar
regulator features such as short circuit and thermal overload
protection are also provided.

•
•
•
•
•
•
•
•
•
•
•

The LM2931 family includes a fixed 5Voutput (±3.8% tolerance for A grade) or an adjustable output with ON/OFF pin.
Both versions are available in a TO-220 power package and
an 8-lead surface mount package. The fixed output version
is also available in the TO-92 plastic package.

Very low quiescent current
Output current in excess of 100 mA
Input-output differential less than 0.6V
Reverse battery protection
60V load dump protection
-50V reverse transient protection
Short circuit protection
Internal thermal overload protection
Mirror-image insertion protection
Available in TO-220, TO-92 or SO-8 packages
Available as adjustable with TTL compatible switch

Output Voltage Options
LM2931T-5.0, LM2931AT-5.0

5V

LM2931Z-5.0, LM2931AZ-5.0
LM2931M-5.0, LM2931AM-5.0
LM2931 CT
LM2931 CM

5V
5V
Adjustable from 3V to 24V
Adjustable from 3V to 24V

Connection Diagrams and Ordering Information
FIXED SV OUTPUT
TO-220 3-Lead Power Package

8-Pln Surface Mount

Llo-!~~IL--l~========~~

TLlH/5254-6

Front View

OUT- Ie

8

GND- 2

7 rGND

GND- 3

6

NC'- 4

5 rNC'

*NC

O U T B IN

~GND

--_..

Order Number LM2931T-S.O or
LM2931AT-S.O
See NS Package Number T03B

TO-92 Plastic Package

~IN

GND
TLlH/5254-8

Bottom View

TL/H/5254-7

= Not intemally connected
Top View

Order Number LM2931M-S.O or
LM2931AM-S.O
See NS Package Number M08A

Order Number LM2931Z-S.0 or
LM2931AZ-S.O
See NS Package Number Z03A

ADJUSTABLE OUTPUT VOLTAGE
TO-220 S-Lead Power Package

8-Pln Surface Mount

[I~o~~JI[~oJI~~~~~ it~~8~f

TL/H/5254-Q

OUT- 10

8 -IN

GND- 2

7 -GND

GND- 3

6 -GND

ADJ - ..4
_ _ _5..- ON/OFF

Front View

TL/H/5254-10

Top View

Order Number LM2931CT
See NS Package Number TOSA

Order Number LM2931CM
See NS Package Number M08A

2-29

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Operating Range
26V
Overvoltage Protection
LM2931A, LM2931CT Adjustable
60V
LM2931
50V

Internal Power Dissipation
(Notes 1 and 3)
Operating Ambient Temperature Range
Maximum Junction Temperature
Storage Temperature Range
Lead Temp. (Soldering, 10 seconds)
ESD Tolerance (Note 4)

Internally Limited
-40'Cto +S5'C
125'C
- 65'C to + 150'C
230'C
2000V

Electrical Characteristics for Fixed 5V Version
VIN = 14V, 10 = 10 mA, TJ = 25'C, C2 = 100,...F (unless otherwise specified) (Note 1)
LM2931A-5.0
Parameter

Conditions
Typ

Output Voltage

5
6.0V ~ VIN ~ 26V, 10 = 100 mA
-40'C ~ Tj ~ 125'C

Line Regulation

9V
6V

~
~

VIN';: 16V
VIN ~ 26V
~

10

~

Typ

Limit
(Note 2)

Units
Limit

5.19
4.81

5.25
4.75

VMAX
VMIN

5.25
4.75

5.5
4.5

VMAX
VMIN

2
4

10
30

mVMAX
mVMAX

14

50

2
4

10
30

14

50

Load Regulation

5 mA

Output Impedance

100 mADC and 10 mArms,
100 Hz-10 kHz

200

Quiescent Current

io ~ 10mA,6V';: VIN ~ 26V
-40'C ~ Tj ~ 125'C
10 = 100 mA, VIN = 14V, Tj = 25'C

0.4

1.0

0.4

15

30
5

15

10 Hz-100 kHz, COUT = 100,...F

500

500

""VrmsMAX

20

20

mV/1000 hr

Output Noise Voltage

100 mA

Limit
(Note 2)

LM2931-5.0

Long Term Stability

200

Ripple Rejection

fo=120Hz

80

55

80

Dropout Voltage

10 = 10mA
10 = 100mA

0.05
0.3

0.2
0.6

0.05
0.3

Maximum Operational
Input Voltage

33

Maximum Line Transient

RL = 5000, Vo ~ 5.5V,
T = 1 mS,T ~ 100ms

Reverse Polarity Input
Voltage, DC

Vo:;' -0.3V, RL = 5000

Reverse Polarity Input
Voltage, Transient

T = 1 ms, T

~

1.0

mAMAX
mAMAX
mAMIN

dBMIN
0.2
0.6

VMAX
VMAX

VM~X

33
26

mVMAX
mOMAX

26

VMIN

70

60

70

50

VMIN

-30

-15

-30

-15

VMIN

-so

-50

-80

-50

VMIN

100 ms, RL = 5000

Note 1: See circuit In Typical Applications. To ensure constsnt junction temperature, low duly cycle pulse lesting is used.
Note 2: All limits are guaranleed for TJ = 25'C (standard type face) or over the full operating Junction temperature range of - 40'C to + 125"C (bold typa faca).
Note 3: The maximum power dissipation Is a function of maximum Junction temperature TJmax, lolal thermal reslstsnce 9JA, and ambient temperature TA. The
maximum allowable power disslpalion at any ambient temparature is Po = (TJmax - TA)/9JA. If this dissipation Is exceeded, the die temperature will rise above
t 50'C and the LM293t will go into thermal shuldown. For the LM2931 in the T0-92 package, 9JA Is 195'C/W; in Ihe SO.a package, 9JA Is 160'C/W. and In the TO·
220 package, 9JA Is 50'C/W. If the TO·220 package Is used with a heat sink, 9JA Is the sum of the package thermal resistance junction·to·case of 3'C/W and the
thermal reslstsnce added by the heat sink and thermal Interface.
Note 4: Human body model. 100 pF discharged through 1.5 kG.

2·30

Electrical Characteristics for Adjustable Version
VIN = 14V, VOUT = 3V, 10 = 10 mA, TJ = 25'C, R1 = 27k, C2 = 100)J.F (unless otherwise specified) (Note 1)
Parameter

Conditions

Reference Voltage

Typ

Limit

Units
Limit

1.20

1.26
1.14

VMAX
VMIN

1.32
1.08

VMAX
VMIN

24
3

VMAX
VMIN
mVIVMAX

'0 s; 100 mA, -40'C S; Tj S; 125'C, R1 = 27k
Measured from VOUT to Adjust Pin
Output Voltage Range

+ 0.6V S; VIN S; 26V

Line Regulation

VOUT

0.2

1.5

Load Regulation

5 mA S; 10 S; 100 mA

0.3

1

Output Impedance

100 mADe and 10 mA rms , 100 Hz-10kHz

40

Quiescent Current

10 = 10mA
10 = 100mA
During Shutdown RL = 500n

0.4
15
0.8

10 Hz-100 kHz

100

)J.VrmslV

0.4

%/1000 hr

Output Noise Voltage
Long Term Stability

%MAX
mnlV

1
1

mAMAX
mA
mAMAX

Ripple Rejection

fa = 120 Hz

0.02

Dropout Voltage

10 S; 10mA
'0 = 100mA

0.05
0.3

0.2
0.6

VMAX
VMAX

33

26

VMIN

70

60

VMIN

-30

-15

VMIN

-80

-50

VMIN

2.0
2.2

1.2
3.25

VMAX
VMIN

20

50

)J.AMAX

Maximum Operational Input
Voltage
Maximum Line Transient

10 = 10 mA, Reference Voltage
T = 1 ms,

T S;

S;

1.5V

100 ms

Reverse Polarity Input
Voltage, DC

Va:;" -0.3V, RL = 500n

Reverse Polarity Input
Voltage, Transient

T = 1 ms, T S; 100 ms, RL = 500n

On/Off Threshold Voltage
On
Off

Vo=3V

On/Off Threshold Current

2·31

%IV

.-

~
'"
:IE

....

r-------------------------------------------------------------------------------------~

Typical Performance Characteristics
Dropout Voltage
0.6

e
!

I
!
I
0

0.5

I I
I

I

OA

-

I..,,..000o

0.3

"...-

0.2

-

0.1
0

Dropout Voltage

I

10 = 100 mA_

I

I

I""'"

6.0

e

0.5

5.0

Q

OA
0.3

i
!

10 = 50mA
10 = 10mA

S

.f

I I

o

40

e

0.2
0.1

V

I

2

Line Transient Response

I

I

o

L~

i
i
a
o

C

500 I-- Ti

!..400

250

30

o

o

10

i

I

u

II
I I

30
25

......

o

o

30

20

-

I--

15

i ':

o

-5

~ ="00'mA - -

Ioji..,.j"

I I

-

~

~=~ ..
10=10mA

-20 -10 0 10 20 30 40 50 60

Input Voltage (VI

-

~

&0

20
15
10

~-

J

-- '--

90

C2 = 100

80

j:
..

I

60

//

v..'
J
.. I

10

100

It

10k lOOk

FJeqUlncy (HzI

75

a:

65
60

i

120

-t

711

50
45

45
1

80

60

:a.
t:

~ 55

~

LM2931·5.0
1o=10mA

50

40

85

TANT

II

55

!ml- r-r-

Ripple Rejection
~F

iii'

C2 = 100 pF AWM

101=

r- ....::

Junction Temperature ('C)

I

75

10=50mA

-40

Ripple Rejection
85

-

o

Output Current (mAl

i

45

Quiescent Current

!

Quiescent Current

30

25

i

30

15

TIme (~.)

~

20

H-I-H-I-M+-H-H
o

YIN = 14V

Input Voltage (VI

35

150

Quiescent Current

I
I

100

'1;t~~~~~:tl

0 I-

(~sl

B300 ~i~ 11 = -40'C

}200

&.0

C2 = l00~FH-+-±-1I-+'+-i

]

45

T· = 8So C
I..L~ ~

1:

40

30

-

JJ

15
Time

Peak Output Current
600

5.0

!~ -40 ~i#+++-+-t--j-ll-+H

...

-2
-20 -10 0 10 20 30 40 50 60
Input VoIIIIge (VI

4.0

Load Transient Response

11._
s'ri
;i
S iiii

VJN • YOUT = IV
C2 = l00~Fjiii"

I

3.0

Input Voltage (V)

-

B

I
2.0

100

8
6

2.0

Output Cumnt (mAl

LM2931·5.0
RL = 5000

~

,.

0

1.0
50

120

Output at Voltage Extremes

J

~

S 3.0
9-

-~

12

e

, ,.,.

& 4.0

Junction TemperatU18 (CI

10

LM2931·5.0
10 = 100 mA

~
~

o

80

Low Voltage Behavior

0.6

1M

10 = 120 Hz

o

25

50

75

100

Output Currant (mAl
TLIHI5254-2

2·32

Typical Performance Characteristics
Operation During Load
Dump

Output Impedance
10

L02'''-'.
~., mA

S

['...

~

~

..eo
5

.. - 150

o

./

0.1

0.01

I

10

100

Ik

10k lOOk

-100 0

0.8

i"o..

0.4
0.3

100

200

300

400

"

o

o

3

6

1.0

~

3.B

:c

3.1
3.4
3.2

!:i
~

2.&

I

2.4

0.7

:

o.a

IS

la

21 24

I
I
I

~

...

r--.
......

0.5

0.4"

0.3
0.2

100

I
I
I

D~:'. :L~OLENDTH

~

[AD

II- LET+"R-

0.4

i

:"'o~

0 C AKO

,-

r" ~
~~

;;;

I
1

0.1

°

o

'0 20 3040 50 60 70 aD 90

AWBIENT TEUPERATURE('e)

Output Capacitor E5R

LU2 31C A~)lST LE

CaUT- 100 l'r
YOASY

10
Dr

3.0
2.8

z

AMSIENT TEWPERATURE ('e)

On/Off Threshold

4.0

0.9

o 10 20 30 40 SO aD 70 aD 90 100

AWBIENT TEWPERATURE (,C)

12

.......

Maximum Power Dissipation
(T0·92)

~i"'o ~'C '" ~T SIN i - i - I(

9

0.9

o
10 20 30 40 SO 80 70 80 90

...i!:~

...... 1-0.,

OUTPUT VOLTAGE (V)

0.1

III

SOD

!2

i"'-

......

1.14

:g

~ NiH~ r 51

~

......

I.Ia

I FIN TE £.IT SIN

0.2

o

I.Ia

Maximum Power Dissipation
(TO·220)

20
la
1&
14
12
10

.....

0.5

~
Ii!

1.20

~

TIWE(m.)

22

0.7

~

1.22

1.10

IW

1.0

.....

1.24

j:!

o

Maximum Power Dissipation

0.8

1.26

III

-2

(50-8)

i'..

r

~

1.12

FREQUENCY (Hz)

0.9

m'

Co·l0DI'F
~ =&000

B
4
2

0

Reference Voltage
1.30
LM2t3IC ADJUST" LE
1,2a

70
aD
50
40
30
20
10

I

V

10'"

'~

STAaI.E
REGION

1

2.2
2.0

1
o

3

1

8

~

~

~

~

20

24

OUTPUT VOLTAGE (V)

40

10

80

100

OUTPUT CURRENT (mA)
TL/H/5254-3

2-33

Typical Applications
LM2931 Fixed Output
VIN
UNREGULATED
INPUT

LM2931 Adjustable Output
Vec

VOUT
REGULATED
OUTPUT

•

AJ
51k

IN

OUT

VOUT

OFF

TLlH/5254-4

ON/OFF

'Required if regulator is located far from power supply filter.

Cl'
0.1 pF ;:~

"C2 must be at least 100 I'F to maintain stability. May be increased without
bound to maintain regulation during transients. Locate as close as possi·
bra to the regulator. This capacitor must be rated over the same operating

LM29JI
ADJUSTABLE

Rl
2Bk

~

ON

(ESR) of this capacitor is critical; see curve.

~C2'

~R2

GND

temperature range as the regulator. The equivalent series resistance

+

;: ' " 100

)

TL/H/5254-5
VOUT

Rl

+

R2

= Reference Voltage X -R-l-

Note: Using 27k for R1 will automatically compensate for BITorS in VOUT due
to the input bias current of the ADJ pin (approximately 1 I'A).

Schematic Diagram
0---------,

V,N 0-....- - - - - - - - - - - - - -.....

Your

.1

5V:28k
ADJ:Oco

lOUT =500 mA

~;

60

w -

!co gz

,

10
5

is

I'"

Load Transient Response
(Vour)
~- 100

~l 50
§el§ 0
~!L5O
g!!i-l00

IV'

Q-l0

10

20 30

40

50

60

0102030405060

TIME I,..)

150 r--r-"""T"--,r--r--r----r.....,
>e 100 I-+-+-~+-+-~-/
50 I--I--+-~+-+-~-/
0
!is -50

i ~~
~~

1-+-+-+-"'-+-+-01
1-+-+-1-+-+-1--1

g !!i-l00 1-+--+-1-+--+-1--1
-1501-+-+-1-+-+-4--1

~! ~~~-+-+--Ir-+-~~

!

i

~6

10

IL

..L

"

I-+-+-~+-+-~-/

1-+-+-1-+-+-+-01

5
OL..-J.-...L....J..-L...--L-J--J

0102030405060

TIME (ps)

0.2

o i""""

0102030405060

TlME(,..)

Load Transient Response
(VsrBY)

!.¥

~

-150
0.8
... 0.6
~i'!! 0.4

a

!:j

60

g

o

>-

20
40
INPUT VOLTAGe IV)

150

,.l-

A

1--

-20

-40 -20

Line Transient Response
(VsrBY)

~§ 0
l'! iC -5

II

~ ~ -10

-2

TIME(,..)

Peak Output Current (Vour)

Peak Output Current (VsrBY)
100

g

...

1.5

~

,

ili

.....====

1.0

e:

!ii
~
i!

JI

=

co 0.5

o

1

~

o

~
10 15 20 25
IIlPUT VOIJAOE IV)

30

80
60

~

I

--

.I

40

20

o

o

10

20 30 40 60
INPUT VOLTAGE IV)

60
TL/H/5232-3

2·39

EI

~
C')

~

::E

r------------------------------------------------------------------------------------------,
Typical Performance Characteristics

(Continued)

....I

Quiescent Current (VOUT)
120
110

c lOO
So 90

i"'

B
!i:

Quiescent Current (VSTBV)

20
10

o~
o 100

.....

II'"

"

I""""""

o

.....
o

-40

~140

I,-lrJv =10 'mA_

r-

IIIIV=O mA

70

'j:

60

co

fll
UI

'"

i

t-

1/

60

-30

10

..iii
..

'"::>

30

~'2O
I! 100

~

80

loUT5DDmA

S

20

lourOmA

40
BO
120 1611
JUNCTION TEMPERATURE (OCI

Quiescent Current (VSTBV)

~

I
I

IST=I'0~ ~

.wi
IrVjOr-

-20 -10 0 10 20 3D 40 5D 60
INPUT VDLTAGE (VI

lOUT =500 mA
C2=10~F r-

'100
lk
FREOUENCY (Hz)

Ripple Rejection (VSTBV)
BO

10=120 Hz

iz

~

60

co

...

60

'"

50

'"

50

~

40

UI

iii 70
:!!.

r--..

z

~
UI

E 40

~

Ii!

30
10k

30

150 300 450 600
OUTPUT CURRENT (mAl

0

Output Impedance

750

Reset on Startup

10

fo=12OHz

70

I"'"--

B

0

",

/
100
lk
. FREOUENCY (Hz)

10k

o

.....

8

ID"C W HEAT SINK

t: :'4Il HEAT ~INK

L

o

012345678
INPUT VOIl'AOE (V)

25

INANITE HEAT SINK

20
18
16
14
12
10

/
TO

5
10
15
20
OUTPUT CURRENT (mil)

Maximum Power
Dissipation (TO-220)
22

_~~=~k

RL=10Q

0.01

-

o

-20 -10 0 10 20 30 40 50 60
INPUT VOLTAGE (VI

co

51 DPEN
VOUT OFF

B

Ripple Rejection (VOUT)

Your

40
BO 120 160
JUNCnDN TEMPERATURE (OC)

9

BO

Vmv ''''''
Imv=10 mil
C3=10"F

~

lOUT =250 mA

--+I~=I50~ -t-r-

10
-40

ISIBV =10 mA
lour =150 mA'=

tt.

40

o

5
10
15
20
25
STANDBY OUTPUT CURRENT (mAl

i ::

r-

40

6D

z

13 20
5

f- -

I I

"
_f--IOUT=500
mA

l:! 50

...V

160

I

Ripple Rejection
BO r

o

Imv=10mA

70

Quiescent Current

Quiescent Current (VSTBV)

'=="

!....

CJ

2DD 300 400 500 6011 700 800
Vour-DUTPUT CURRENT (mAl

51 OPEN
YoUT OFF

/
./

I

iS ::

!z

S10PEN
YoUT DFF

I
II

80
70
60
50

Quiescent Current (VOUT)
80

5

II

Imv=10 mA

.....

l-

I l

o 10 20 lO 40 50 60 70 80 90 100
AMBIENT TEMPERATURE.(CC)

TL/H/5232-4

2-40

Load Regulation: The change in output voltage for a
change in load current at constant chip temperature,

Typical Performance
Characteristics (Continued)

Long Term Stability: Output voltage stability under accelerated life-test conditions after 1000 hours with maximum
rated voltage and junction temperature.
Output Noise Voltage: The rms AC voltage at the output,
with constant load and no input ripple, measured over a
specified frequency range .
Quiescent Current: The part of the positive input current
that does not contribute to the positive load current. The
regulator ground lead current.

Output Capacitor ESR
(Standby Output, Pin 5)

g

100

~

10

...uz

COUT

~~

~

~

I-

z

~::>

B

////, f0/- ~

~

'"~
ffi
VI

0.1

0.01

=10 ~f

'r/

/,

~

~//

o

//~

STABLE
REGION

~
~

Ripple ReJection: The ratio of the peak-to-peak input ripple
voltage to the peak-to-peak output ripple voltage.
Temperature Stability of Vo: The percentage change in
output voltage for a thermal variation from room temperature to either temperature extreme.

"-

/~

,///J./// '//

2

8
OUTPUT CURRENT (rnA)

Application Hints

10

EXTERNAL CAPACITORS
The LM2935 output capacitors are required for stability.
Without them, the regulator outputs will oscillate, sometimes
by many volts. Though the 10p.F shown are the minimum
recommended values, actual size and type may vary depending upon the application load and temperature range.
Capacitor effective series resistance (ESR) also factors in
the IC stability. Since ESR varies from one brand to the
next, some bench work may be required to determine the
minimum capacitor value to use in production. Worst-case Is
usually determined at the minimum ambient temperature
and maximum load expected.

TL/H/5232-9

Output Capacitor ESR
(Main Output, Pin 2)

= 10~f

COUT

""'-

%'~ ~

~,
~.

' / / ' / / / ' / / / '//~

STABLE
REGION

~/, ' / / / .

§

~

/// ///,

1// .%:

Output capacitors can be increased in size to any desired
value above the minimum. One possible purpose of this
would be to maintain the output voltage during brief conditions of negative input transients that might be characteristic of a particular system.

0.1

~

::>

B

0.01

a

100

200

300

400

500

Capacitors must also be rated at all ambient temperatures
expected in the system. Many aluminum type electrolytics
will freeze at temperatures less than -30'C, reducing their
effective capacitance to zero. To maintain regulator stability
down to -40'C, capacitors rated at that temperature (such
as tantalums) must be used.
No capacitor must be attached to the ON/OFF and ERROR
FLAG pin. Due to the internal circuits of the IC, oscillation on
this pin could result.

OUTPUT CURRENT (mA)
TL/H/5232-10

Definition of Terms
Dropout Voltage: The input-output voltage differential at
which the circuit ceases to regulate against further reduction in input voltage. Measured when the output voltage has
dropped 100 mV from the nominal value obtained at 14V
input, dropout voltage is dependent upon load current and
junction temperature.
Input Voltage: The DC voltage applied to the input terminals with respect to ground.
Input-Output Differential: The voltage difference between
the unregulated input voltage and the regulated output voltage for which the regulator will operate.
Line Regulation: The change In output voltage for a
change In the input voltage. The measurement is made under conditions of low dissipation or by using pulse techniques such that the average chip temperature is not significantly affected.

STANDBY OUTPUT
The LM2935 differs from most fixed voltage regulators in
that it is equipped with two regulator outputs instead of one.
The additional output is intended for use in systems requiring standby memory circuits. While the high current regulator output can be controlled with the ON/OFF pin described
below, the standby output remains on under all conditions
as long as sufficient input voltage is applied to the IC. Thus,
memory and other circuits powered by this output remain
unaffected by positive line transients, thermal shutdown,
etc.
The standby regulator circuit is designed so that the quiescent current to the IC Is very low «3 mA) when the other
regulator output is off.

2-41

•

~r---------------------------------------------------------------~

re

:E

.....

Application Hints (Continued)
In applications where the standby output is not needed, it
may be disabled by connecting a resistor from the standby
output to the supply voltage. This eliminates the need for a
more expensive capacitor on the output to prevent unwanted oscillations. The value of the resistor depends upon the
minimum input voltage expected for a given system. Since
the standby output is shunted with an internal 5.7V zener
(Figure 3), the current through the external resistor should
be sufficient to bias R2 and R3 up to this point. Approximately 60 ",A will suffice, resulting in a 10k external resistor
for most applications (Figure 4).

ON/OFF AND ERROR FLAG PIN
This pin has the ability to serve a dual purpose if
desired. When controlled in the manner shown in Figure 1
(common in automotive systems where S1 is the ignition
switch), the pin also serves as an output flag that is active
low whenever a fault condition is detected with the high
current regulated output. In other words, under normal
operating conditions, the output voltage of this pin is high
(5V). This is set by an internal clamp. If the high current
output becomes unregulated for any reason (line transients,
short circuit, thermal shutdown, low input voltage, etc.) the
pin switches to the active low state, and is capable of sinking several milliamps. This output signal can be used to initiate any reset or start-up procedure that may be required of
the system.

HD
10k

The ON/OFF pin can also be driven directly from open collector logiC circuits. The only requirement is that the 20k
pull-up resistor remain in place (Figure 5). This will not affect
the logic gate since the voltage on this pin is limited by the
internal clamp in the LM2935 to 5V.

STANDBY
OUTPUT
LM2935

I

...b. C3
l'
I

~

~~k
CMOS MM74C04
OR EQUIVALENT

TLlH/5232-6

DELAYED
RESET
OUT

FIGURE 4. Disabling Standby Output to Eliminate C3
HIGH CURRENT OUTPUT
Unlike the standby regulated output, which must remain on
whenever possible, the high current regulated output is fault
protected against overvoltage and also incorporates thermal shutdown. If the input voltage rises above approximately 30V (e.g., load dump), this output will automatically shutdown. This protects the internal circuitry and enables the IC
to survive higher voltage transients than would otherwise be
expected. Thermal shutdown is effective against die overheating since the high current output is the dominant source
of power dissipation in the IC.

Rl

20k

TL/H/5232-11

FIGURE 6. Reset Pulse on Power-Up
(with approximately 300 ms delay)

LM2935

SWITCH/
DM7405

LM2935
4 SWITCHI
RESET

RESET
TLlH/5232-7

FIGURE 5. Controlling ON/OFF Terminal with
a Typical Open Collector Logic Gate

2-42

o
:::;"

n

SWITCH/RESET

•

c:

::i:'

VI:.

en
n

:::T
CD

3

a5"
P17

+--~tp,B

~

VOUl

'"

R33

R30

R3

R31

R4

N28

GND

TUH/5232-5

FIGURE 3

SC6~W'

II

~

fJ
::i

.----------------------------------------------------------------------------,

..... ~National
~ semiconductor

LM2936 Ultra-Low Quiescent Current 5V Regulator
General Description

Features

The LM2936 ultra-low quiescent current regulator features
low dropout voltage and low current in the standby mode.
With less than 15 p,A quiescent current at a 100 p,A load,
the LM2936 is ideally suited for automotive and other battery operated systems. The LM2936 retains all of the features that are common to low dropout regulators including a
low dropout PNP pass device, short circuit protection, reverse battery protection, and thermal shutdown. The
LM2936 has a 40V operating voltage limit, -40"C to
+125'C operating temperature range, and ±3% output
voltage tolerance over the entire output current, Input voltage, and temperature range. The LM2936 is available in
both a TO-92 package and an a-pin surface mount package
with a fixed 5V output.

• Ultra low quiescent current (10 ~ 15 p,A for
10 ~ 100 p,A)
• Fixed 5V, 50 mA output
• Output tolerance ±3% over line, load, and temperature
• Dropout voltage typically 200 mV @ 10 = 50 mA
• Reverse battery protection
• - 50V reverse transient protection
• Internal short circuit current limit
• Internal thermal shutdown protection
• 40V operating voltage limit

Typical Application

Input- -

VIN

LM2936

• Required If regulator Is located more than 2" from power supply filter
capacitor•
.. Required for stability. Must be rated for 10 ".F minimum over Intended
operating temperature range. Effective series resistance (ESR) Is Critical,
see curve. Locate capacHor as close as possible to the regulator output and
ground pins. CapaCitance may be Increased without bound.

10

Vo .....'""'4~Output

TL/H/9759-1

Connection Diagrams
TO-92 Plastic Package (Z)

S-PlnSO(M)
IN

GND

GND

NC

GND

GND

NC

o

TL/H/9759-2

BoHomVlew
Order Number LM2936Z-S.0
See NS Package Number Z03A

OUT

TLlH/9759-e

Top View

Order Number LM2936M-S.O
See NS Package Number MOSA

2-44

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
+60V, -50V
Input Voltage (Survival)
ESD Susceptability (Note 2)
2000V
Internally limited
Power Dissipation (Note 3)
Junction Temperature (TJmax)

Storage Temperature Range
Lead Temperature (Soldering, 10 sec.)

- 65'C to + 150'C
260'C

Operating Ratings
Operating Temperature Range
Maximum Input Voltage (Operational)

-40'Cto + 125'C
40V

150'C

Electrical Characteristics
VIN = 14V, 10 = 10 mA, TJ = 25'C, unless otherwise specified. Boldface limits apply over entire operating temperature range
Parameter
Output Voltage

Line Regulation
Load Regulation

Typical
(Note 4)

Conditions

Tested
Limit
(Note 5)

Design
Limit
(Note 6)

Units

4.85

Vmin
V

5.15

Vmax

5.5V s;: VIN s;: 26V,
10 s;: 50 mA (Note 7)

5

9V s;: VIN s;: 16V

5

10

6V s;: VIN s;: 40V, 10 = 1 mA

10

30

100,...A s;: 10 s;: 5 mA

10

30

5 mA s;: 10 s;: 50 mA

10

30

mVmax
mVmax

Output Impedance

10 = 30 mAdc and 10 mArms,
f = 1000Hz

Quiescent Current

10 = 100 ,...A, 8V s;: VIN s;: 24V

9

15

,...Amax

10 = 10 mA, 8V s;: VIN s;: 24V

0.20

0.50

mAmax

10 = 50mA,8V s;: VIN s;: 24V

1.5

2.5

mAmax

10 Hz-l00 kHz

500

Output Noise Voltage

450

Long Term Stability
Ripple Rejection
Dropout Voltage

mn

""Vrms
mV/l000 Hr

20
Vripple = 1 Vrms, fripple = 120 Hz
10 = 100,...A

60

40

0.05

0.10

dBmin
Vmax

10 = 50mA

0.20

0.40

Vmax

-15

Vmin

-80

-50

Vmin

-0.1

-600

,...Amax

~

Reverse Polarity
DC Input Voltage

RL = 500n, Vo

Reverse Polarity
Transient Input Voltage

RL

Output Leakage with
Reverse Polarity Input

VIN = -15V, RL = 500n

= 500n, T

-0.3V

= 1 ms

Maximum Line Transient

RL = 500n, Vo s;: 5.5V, T = 40 ms

Short Circuit
Current

Vo

= OV

120

60

Vmin

250

mAmax

65
mAmin
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. DC and AC electrical specifications do not apply when operating
the device beyond its specified operating ratings.
Note 2: Human body model, 100 pF discharge through a 1.5 kfl resistor.
Note 3: The maximum power dissipation is a function of TJmax. 9JA. and TA' The maximum allowable power dissipation at any ambient temperature is
Po = (TJmax - TA)10JA. If this dissipation is exceeded, the die temperature will rise above 150'C and the lM2936 will go into thenmal shutdown. For the
lM2936Z, the junction·to·ambient thermal resistance (0JN is 195'CIW. For tha lM2936M, 8/a is 160'CIW.

Note 4: Typicals are at 25'C (unlass otharwise specifiad) and represent tha most likely parametriC nonm.
Note 5: Tested limits ara guarantaed to National's AOQl (Avaraga OutgOing Quality laval) and 100% tasted.
Note 6: Design limits are guarantaed to National's AOQl (Averaga Outgoing Quality level) but not 100% tested.
Note 7: To ensure constant junction temperature, pulse testing is used.

2-45

~

re
:!i

Typical Performance Characteristics
Maximum Power
Dissipation (TO·92)

Dropout Voltage

1.0
0.9
0.9

Dropout Voltage

Q.5

Q.5

E
~

0.7

D.3

D.6
Q.5

D.4
D.3
D.2

D.2

I"""

,..-

10UT:;!I,!!!A. ~

-

lour = 10mA

0.11"""

OJ)

120

I I

50

5

D.2

100

,...

0

,!.

0.1

o

150

---

10

20

30

40

Quiescent Current
V,N -14V
I- TJ=2SCC

16
14

12
10

I I

1o=100J'A

AIo=IOOJ'A

10

jlo=OI'Aj

I I

-10
-20 -10 0

o

10 20 30 40 50 60

,

!

-'

2S
2.Q

I

1.5

Io=SOmA

1.0
Q.5

-0.5
-20

Io J'OmA

V

o
-10

10

INPUT VOLTAGE (V)

ISO

o

2!J

1.11
1.6

20

30

/

40

50

Output CapaCitor ESA
100 r.:"---,=....,..,.""T"""""--:-:~

t.4

I~

DB
D.6

'"'"

D.4
D.2

1:1

10

./

OUTPUT CURRENT (mA)

I
Io~SO~A

IN= 14V

-

-'

o

Quiescent Current
2.Q

TJ=2SCC

3.0

100

JUNCTION TEMPERATURE(CC)

Quiescent Current
3.5

So

-50

INPUT VOLTAGE (V)

40

50

OUTPUT CURRENT (mA)

Quiescent Current

11o=lmA

20

5

20
VIN=14V
18

J=2S"!

nl I

40

30

D.3

JUNCTION TEMPERATURE(CC)

Quiescent Current
60

50

-50

AMBIENT TEMPERATURE (CC)

~

o

OJ)

80

-«I

~

~

0.1

TJ=dscc
D.4

1.2
1.0

o

-50

1o=10mA
0.001
50

100

JUNCTION TEMPERATURE (CC)

150

L-L.....I-"....L....J..-'--'--'-...J.......J

o

10

20

30

40

50

OUTPUT CURRENT (mA)
TL/H/9759-3

2·46

Typical Performance Characteristics (Continued)
Peak Output Current

Peak Output Current

250

!

ISO

!5

!
ffi

I

f-~~

100

5
"
~

50

o
o

J

~

a

IS

20

CoUT=IOpF
~~O.1)4 10=IOmA
~ ~ 0.D2 VIN =14V

o

Output at
Voltage Extremes
12
Rt. =50011
T =25'C

!z

§"

V

I
I
10

Load Translent,Response

~~1J.04

~~ 0.D'J.

s~

0

~c-o.D'J.
-D.04

-D.06

~

!ii!~

1\

\

\

/

20

30

40

50

i

40

~

10

50

60

1.0

2.D

TlMEtus)

3.0

4.D

INPUT VOLTAGE (V)

Ik

10k lOOk

1M

Output Impedance

g

1/
(
40

100

FREQUENCY (Hz)

/

1.0
30

\ I
I

2.0

S

0.5

I
s.o

I

VIN =14V,
'0=30mA
COUT=IOpF

5.0

~

5
"
10 20

i\

30

60

40
30

0

iii

10.0

'O=IOmA
TJ =25CC

I
I-J

9~ 2010

B

60

Low Voltage Behavior

s.o

CoUT=IOpF

250

I

INPUT VOLTAGE (v)

TIME (m,)

D.06

200

20

-10 0

1.2 1.4

ISO

V'N=14V
1Q=IOmA
70 Cour= 10pF

50

-2
1.0

,00

Ripple Rejection
80

0

0.4 0.6 DB

50

OUTPUT CURRENT(mA)

~I=

D.2

I

o

10

5-11.02

~

I

50r-r-+-+-~-r-r-+~

JUNCTION TEMPERATURE (CC)

D.06

an

/'

/'

25

Line Transient Response

~~

)

150r-r-+-+-~-r-r-+~

~ 100~~t:~~~~:t:j
"~

10

YIN=1.4V

200l-HHHHHHH

INPUT VOLTAGE (V)

~

TJ=25'C

V'N=14V

200

ia

Current Limit

250~~~~'--r-r-r-'

TJ=25CC

h
/ \

1.0

~

0.2
0.1

6.D

I

10

100

Ik

10k lOOk

III

FREQUENCY (Hz)
TL/H/9759-4

Applications Information
Under conditions of higher ambient temperatures, the voltage and current calculated in the previous examples will
drop. For instance, at the maximum ambient of 12S'C the
LM2936 can only dissipate 128 mW, limiting the Input voltage to 7.34V for a 50 mA load, or 3.5 mA output current for
a 40V input.

Unlike other PNP low dropout regulators, the LM2936 remains fully operational to 40V. Owing to power dissipation
characteristics of the TO-92 package, full output current
cannot be guaranteed for all combinations of ambient temperature and input voltage. As an example, consider an
LM2936 operating at 2S'C ambient. Using the formula for
maximum allowable power dissipation given in Note 3, we
find that PO max = 641 mW at 25'C. Including the small
contribution of the quiescent current to total power dissipation the maximum input voltage (while still delivering 50 mA
output current) is 17.3V. The device will go into thermal
shutdown if it attempts to deliver full output current with an
input voltage of more than 17.3V. Similarly, at 40V input and
25'C ambient the LM2936 can deliver 18 mA maximum.

While the LM2936 maintains regulation to 60V, it will not
withstand a short circuit above 40V because of safe operating area limitations in the internal PNP pass device. Above
60V the LM2936 will break down with catastrophic effects
on the regulator and possibly the load as well. Do not use
this device in a design where the input operating voltage
may exceed 40V, or where transients are likely to exceed
60V.

2-47

•

LM2936

Q~

049-1

'I

k

r--

I

~

~

t

t

051

~ 052

~ ~.
Z2

,j,..
(X)

02

R3

R5

~

1M'

'1

O~

:r

CD

3

....048

017

~

08

"'1-

-I
-I

:t
025

1

~

O~

044

~35

Cl
039

~43

028

~

.---

~:R13

'~'~"

cjii"

Al

037

038

a
n"
CQ

R15

07

053t

055

~

O~

..,!!,15

06

03

05~

036

R6

-

en
n
:::r

~47

Rll

r-

01
I\)

~

~~11

-I:

iD

::l

R12

.1-:::

09

~"

1*"Q46

I.S"

~

R4

O~

~020

t

.....

I

~r

~
~

04

I ....

"'-

R7

05H

'I

I

~, J,J,

~

D4

Co

'I

m
.a
c

r-

*

3

R18

t
R8

~

~
a.A
IGNol

~3
~

~7

R2

jGf

V'

Rl0
----

:-±

040
R14

O~.1""" 042

1.1 ~ 1

R17

_ _R~6~1i'

TUH/9759-5

r-------------------------------------------------------------------------,

~National

N

LM2937 500 mA Low Dropout Regulator
General Description

Features

The LM2937 is a positive voltage regulator capable of supplying up to 500 rnA of load current. The use of a PNP
power transistor provides a low dropout voltage characteristic. With a load current of 500 rnA the minimum input to
output voltage differential required for the output to remain
in regulation Is typically 0.5V (1V guaranteed maximum over
the full operating temperature range). Special circuitry has
been Incorporated to minimize the quiescent current to typically only lOrnA with a full 500 rnA load current when the
Input to output voltage differential is greater than 3V.
The LM2937 requires an output bypass capacitor for stability. As with most low dropout regulators, the ESR of this
capacitor remains a critical design parameter, but the
LM2937 includes special compensation circuitry that relaxes ESR requirements. The LM2937 is stable for all ESR
below 30. This allows the use of low ESR chip capacitors.
Ideally suited for automotive applications, the LM2937 will
protect Itself and any load circuitry from reverse battery connections, two-battery jumps and up to + BOV/- 50V load
dump transients. Familiar regulator features such as short
circuit and thermal shutdown protection are also built in.

• Fully specified for operation over - 40·C to + 125·C
• Output current in excess of 500 rnA
• Output trimmed for 5% tolerance under all operating
conditions
• Typical dropout voltage of 0.5V at full rated load
current
• Wide output capacitor ESR range, up to 30
• Internal short circuit and thermal overload protection
• Reverse battery protection
• BOV input transient protection
• Mirror image Insertion protection

Output Voltages
LM2937ET-5.0
LM2937ET-B.O
LM2937ET-l0
LM2937ET-12
LM2937ET-15

5V
BV
10V
12V
15V

Typical Application
'Required II the regulator Is located more than 3 Inches Irom the power
supply filter capacitors.

1

3~FI

YIN

I
I

I
I

1
Jl'Q It~~TF

LM2937

is:

B
......

~ Semiconductor

UNREGULATED
INPUT

~

YOUT

REGULATED
OUTPUT

"Required lor stability. Coul must be at lasst 10 p.F (over the lull expected
operating temperature range) and located as close as possible to the regula·
tor. The equivalent series resistance, ESR, 01 this capacitor may be as high
as 30.

TLlH/tt28D-t

Connection Diagram and Ordering Information
TO-220 Plastic Package

Order Number LM2937ET-5.0,
LM2937ET-a.O, LM2937ET-10, LM2937ET-12,
or LM2937ET-15
See NS Package Number T03B
TLlHI1 t 280-2

Front View

2-49

Absolute Maximum Ratings

Operating Conditions (Note 1)

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
Continuous
26V
Transient (t ,;;; 100 ms)
60V
Internally Limited
Internal Power Dissipation (Note 2)
Maximum Junction Temperature
150'C
Storage Temperature Range
- 65'C to
Lead Temperature (Soldering, 10 seconds)

Temperature Range (TJ) (Note 2)
Maximum Input Voltage

-40'C to

+ 125'C
26V

+ 150'C
230'C

ESD Susceptibility (Note 3)

2kV

Electrical Characteristics

VIN = VNOM + 5V (Note 4), lOUT = 500 mA, COUT = 10 ",F unless otherwise indicated. Boldface limits apply over the
entire operating temperature range, - 40'C ,;;; T .. ,;;; + 125'C, all other specifications are for TA = TJ = 25'C.
5V

Output Voltage (VOUT)
Parameter
Output Voltage

Conditions

Typ

5 mA ,;;; lOUT';;; 0.5A
5.00

BV
Limit

Typ

10V
Limit

Typ

Units
Limit

10.50

V(Min)
V(Min)
V(Max)
V(Max)

4.85

7.76

9.70

4.75

7.60

9.50

5.15

8.00

8.24

10.00

8.40

5.25

10.30

Line Regulation

(VOUT + 2V) ,;;; VIN ,;;; 26V,
lOUT = SmA

15

50

24

80

30

100

mV(Max)

Load Regulation

S mA ,;;; lOUT';;; O.SA

S

50

8

80

10

100

mV(Max)

Quiescent Current

(VOUT + 2V) ,;;; VIN ,;;; 26V,
lOUT = SmA

2

10

2

10

2

10

mA(Max)

10

20

10

20

10

20

mA(Max)

VIN = (VOUT
lOUT = O.SA

+ SV),

Output Noise
Voltage

10 Hz-100 kHz
lOUT = SmA

Long Term Stability

1000 Hrs.

Dropout Voltage

lOUT
lOUT

=
=

1S0
20

tf

300

32

",Vrms

40

mV

SOOmA

O.S

1.0

O.S

1.0

O.S

1.0

V(Max)

SOmA

110

250

110

250

110

250

mV(Max)

1.0

0.6

1.0

0.6

1.0

0.6

A(Min)

7S

60

7S

60

75

60

V(Min)

26

V(Min)

Short-Circuit Current
Peak Line Transient
Voltage

240

< 100 ms, RL =

100n

Maximum Operational
Input Voltage

26

Reverse DC
Input Voltage

VOUT ~ -0.6V, RL = 100n

Reverse Transient
Input Voltage

t,. < 1 mS,RL = 100n

26

-30

-15

-30

-15

-30

-15

V(Min)

-7S

-50

-7S

-50

-7S

-50

V(Min)

2-S0

Electrical Characteristics

VIN = VNOM + 5V (Note 4), lOUT = 500 mA, COUT = 10 p.F unless otherwise indicated. Boldface limits apply over the
entire operating temperature range, - 40'C ,;: T.. ,;: + 125'C, all other specifications are for TA = TJ = 25'C.
Output Voltage (VOUT)

12V

15V

Units

Typ

Limit

Typ

12.00

11.64
11.40
12.36
12.60

1S.00

14.S5
14.25
15.45
15.75

V (Min)
V(Min)
V(Max)
V(Max)

(VOUT + 2V) ,;; VIN ,;: 26V,
lOUT = SmA

36

120

45

150

mV(Max)

Load Regulation

S mA ,;: lOUT';: 0.5A

12

120

1S

150

mV(Max)

Quiescent Current

(YOUT + 2V) ,;: VIN ,;: 26V,
lOUT = SmA

2

10

2

10

mA(Max)

10

20

10

20

mA(Max)

Parameter

Output Voltage

Line Regulation

Conditions

5 mA ,;; lOUT';: 0.5A

VIN = (VOUT
lOUT = O.SA

+ SV),

Limit

Output Noise
Voltage

10 Hz-100 kHz,
lOUT = SmA

Long Term Stability

1000 Hrs.

44

Dropout Voltage

lOUT = 500mA

0.5

1.0

0.5

1.0

V(Max)

lOUT = 50mA

110

250

110

250

mV(Max)

1.0

0.6

1.0

0.6

A(Min)

75

60

75

60

V(Min)

26

V(Min)

360

Short-Circuit Current
Peak Line Transient
Voltage

t,

< 100 ms, RL =

100n

Maximum Operational
Input Voltage

56

26

Reverse DC
Input Voltage

VOUT;;' -0.6V, RL = 100n

Reverse Transient
Input Voltage

tr

< 1 ms, RL

= 100n

p.Vrms

4S0

mV

-30

-15

-30

-15

V(Min)

-75

-50

-75

-50

V(Min)

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Electrical specifications do not apply when operating the device
outside of its rated Operating Conditions.

Nole 2: The maximum allowable power dissipation at any ambient temperature Is PMAX = (125 - T/JIOJA. where 125 is the maximum junction temperature lor
operation, TAis the ambient temperature. and 0JA is the junction-tcrambient thermal resistance. If this diSSipation is exceeded, the die temperature will rise above
125'C and the electrical specifications do not apply. If the die temperaMe rises above 150'C. the LM2937 will go into thermal shutdown. For the LM2937. the
junction-lo·ambient thermal resistance 0JA is 65'C/W. When used with a heatsink. OJA is the sum of the LM2937 junction-la-case thermal resistance 8JC 01 3'C/W
and the heatsink case-te-ambiant thermal resistance.

Note 3: ESO raling is based on the hUman body model. 100 pF discharged through 1.5 kll.
Note 4: Typicals are at TJ = 25°C and represent the most likely parametric norm.

2-51

•

Typical Performance Characteristics
Dropout Voltage vs
Output Current

Dropout Voltage vs
Temperature

0.9
0.8
~

~~
5
12

!!l

1.0
0.9
0.8
E 0.7
0.6
~ 0.5
0.4
~
0.3
i,..0.2
0.1
0.0

TJ = 25 0 C

0.7
0.8
0.4
0.2
0.1
o

V

V

V

...,.

0.3

o

...,.

~
!!l

/'
200

300

SOO

400

....

0.25A

O.OSA

f--

80

120

100
90
':< 80
70
60
i3 50
40
30
S
a 20
10

10..

250mA

-

8

I-

40

Line Transient Response

0

-

VOUT = 5V
lOUT = 50 rnA
TA = 25°C

\.

20

30

50

5

10

IS

20

25

30

-1

1.0

~

~

0.1

22
20
18
16
14
12
10

III

~

0.01

10k

FREQUENCY (Hz)

lOOk

1M

300

400

500

loUT = SOmA
YOUT " 5V

50

l-HittIIi-ltHltt+

40

l-HittIII-++_+
10

3:

ii3

10 oC/W HEAT SINK

5
~
0

......
\

-40

lk

10k

lOOk

1M

Peak Output Current
1.5

\

r.....

100

FREQUENCY (Hz)

INfiNITE HEAT SINK

NO HEAT SINK

lk

70

0

1.0

-

V,. = 14V

O.S

i'.

o
100

200

Ripple Rejection
VIN = IOV

Maximum Power
Dissipation (TO-220)

Output Impedance

10

100

T1ME (1001")

g

"

OUTPUT CURRENT (mA)

I--/r-+-+-~....I-+-I

-50

60

tour.

SV

~-~

/

o
o

35

f-+-+-+--t--I-+--i

50

TINE (1'.)

VII.f. 14V
10 IJ.f TAMT.
~UT = 25 rnA
Hl-ffll/l-tHl~
VOUT = SV

CII

= 25 0 C

CauT. 10""r

~..§

~~

= 14V

0.05A

~>'

~~

40

TJ

Load Transient Response

g 2!i

,r

10

V,N

VOUT

INPUT VOLTAGE (V)

40

120

V

[,

o

80

Quiescent Current vs
Output Current

/

TEMPERATURE (OC)

\

40

TEMPERATURE (Oc)

0.25A

o

120

80

f-+-+-+-++-+--+-+--i

-40

O.SA

11

o
-40

40

10

~

SmA

f-t-t-t-t-+-+-+-+-l
I-t-t-t-t-+-+-+-+-l

4.96
4.94
4.92

VOUT = SV
fA = 25°C

.s
SOOmA

l-6.j.o,*,,***4d-l

5.00

Quiescent Current vs
Input Voltage

20

f--

f-+-+-+-++-+--+-+--i
f-+-+-+-++-+--+-+--i

5.02

TEMPERATURE (OC)

Quiescent Current vs
Temperature

~
o

~
~

~

5.061-+-+-+-+++-+-+-1

5.04

~90~~~~~~~~~

o

-40

OUTPUT CURRENT (mA)

10

E

r--

100

-10

...,.

0.5A

~

r-r-.,.-..,--,---,--,-....,....,.-,
I\. = loon +-t--I--+-t--i

5.10
5.08

I

~

0.5

Output Voltage vs
Temperature

o
40

80

120

AMBIENT TEMPERATURE (OC)

-40

40

80

120

TEMPERATURE (Oe)
TL/H111280-3

2-52

Typical Performance Characteristics
Low Voltage Behavior
loUT = 500 rnA

TJ

= 25°C

/

VOUT = 5V

V
~

/

1\

20

I

~~
~
50

I

-30 -20 -10

0

~~

10

20

INPUT VOLTAGE (V)

10

12

12V

/
o

14

6

12

15

18

Output Capacitor ESR

g

100
CoUT

~
~

~

/

9

INPUT VOLTAGE (V)

VOUT = 15V

12

~

I
I

-2

= lOon

~

Your = 5V

J

~

~

1(.1

VOUT = BV

Your

o
8

1\

=I~V

A
/f =II

/

I

J

16

Vou;' 10V

~

_

VOUT

12

Output at Voltage
Extremes

I I

= loon

~
g

INPUT VOLTAGE (V)

Output at Voltage
Extremes
10

t-~
= 8V

~

/

INPUT VOLTAGE (V)

12

VOUTI

'OUT = 500 mA
TJ = 25°C

15

I
o
o

4

= 10V

I ~I

A

~
3

18

I

Your

10

~~

J

I

'oUT = 500 rnA
TJ = 25·C--

12

/

2

Low Voltage Behavior

Low Voltage Behavior
14

~

o
o

(Continued)

Ifl

~

VOUT = 12V

~

=

10)lF

Your = SV

I:l

~

J

'"

:>

S

-4
30

40

-30 -20 -10

0

10

20

INPUT VOLTAGE (V)

30

40

100

200

300

400

500

OUTPUT CURRENT (rnA)
TLlH/11280-4

2-53

o ,------------------------------------------------------------------,

i:i
C)

~National

~ Semiconductor

~

;

....

LM2940/LM2940C 1A Low Dropout Regulator
General Description
The LM2940/LM2940C positive voltage regulator features
insertion. Familiar regulator features such as short circuit
the ability to source 1A of output current with a dropout . and thermal overload protection are also provided.
voltage of typically 0.5V and a maximum of 1V over the
entire temperature range. Furthermore, a quiescent current
Features
reduction circuit has been included which reduces the
• Dropout voltage typically 0.5V @Io = 1A
ground current when the differential between the input volt• Output current in excess of 1A
age and the output voltage exceeds approximately 3V. The
• Output voltage trimmed before assembly
quiescent current with 1A of output current and an input-out• Reverse battery protection
put differential of 5V is therefore only 30 mAo Higher quies• Internal short circuit current limit
cent currents only exist when the regulator is in the dropout
• Mirror image insertion protection
mode (VIN - VOUT :;;: 3V).
• P+ Product Enhancement tested
DeSigned also for vehicular applications, the LM29401
LM2940C and all regulated circuitry are protected from reOutput Voltages
Device
Package
verse battery installations or 2-battery jumps. During line
transients, such as load dump when the input voltage can
TO-220
5, 12, 15
LM2940CT
momentarily exceed the specified maximum operating voltLM2940T
5,8,9,10,12
TO-220
age, the regulator will' automatically shut down to protect
both the internal circuits and the load. The LM29401
TO-3
5,8,12.15
LM2940K/883'
LM2940C cannot be harmed by temporary mirror-image
• Available only as a military specified device.

Equivalent Schematic Diagram
r------t-------------------------------------------------------.---1~~~N

...----1"'"""+-=--t----+-----1-----ir--+H..JlIluT

TL/H/8822- 1

Order Number LM2940T-S.O, LM2940T-8.0, LM2940T-9.0,
LM2940T-10, LM2940T-12, LM2940CT-S.O, LM2940CT-12, LM2940CT-1S,
LM2940K-S.0/883, LM2940K-8.0/883, LM2940K-12/883 or LM2940K-1S/883
See NS Package Number K02A or T03B
2-54

Absolute Maximum Ratings

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
(Note 2)
Input Voltage (Survival Voltage)
LM2940T, T:s: 100 ms
60V
LM2940K/883, T :s: 20 ms
40V
LM2940CT, T :s: 1 ms
45V
Internal Power Dissipation (Note 3)
Internally Limited
Maximum Junction Temperature
150·C
-65·C:s: TJ:S: +150·C
Storage Temperature Range

Lead Temperature (Soldering. 10 seconds)
TO-3 (K) Package
TO-220 (T) Package
ESD Susceptibility (Note 4)

300·C
260·C
2kV

Operating Conditions (Note 1)
Input Voltage
Temperature Range
LM2940K/883
LM2940T
LM2940CT

26V
-55·C:s: TA:S: 125·C
-40·C:s: TA:S: 125·C
O·C:S: TA:S: 125·C

Electrical Characteristics
VIN = Vo + 5V. 10 = lA, Co = 22 ,...F, unless otherwise specified. Boldface limits apply over the entire operating
temperature range of the indicated device. All other specifications apply for T A = TJ = 25·C.
Output Voltage (Vo)

Parameter

Conditions

SV

5V

LM2940T-5.0
LM2940K-5.0/SS3
LM2940T-S.O LM2940K-S.0/SS3
LM2940CT-5.0
Typ
Limit
Limit
Limit
Limit
Typ
(Note 6)
(Note 5)
(Note 6)
(Note 5)
9.4V :S: VIN :S: 26V

6.25V :S: VIN :S: 26V
Output Voltage

5mA:S:lo:S:1A

5.00

Line Regulation Vo + 2V :S: VIN :S: 26V,
20
10 = 5mA
Load Regulation 50 mA:S: 10 :S: lA
LM2940, LM2940/883
LM2940C

35
35

Output
Impedance

100mADCand
20mArms,
fo = 120 Hz

35

Quiescent
Current

Vo +2V:s: VIN :S: 26V,
10 = 5mA
LM2940, LM2940/883
LM2940C

Output Noise
Voltage

Units

4.85/4.75
5.15/5.25

4.85/4.75
5.15/5.25

8.00

7.7617.60
8.24/8.40

7.7617.60
8.24/8.40

VMIN
VMAX

50

40/50

20

80

50/80

mVMAX

50/80
50

50/100

55

80/130

80/130

mVMAX
mVMAX

1000/1000

55

1000/1000

mn.

10
10

15/20
15

15/20

10

15/20

15/20

mAMAX
mAMAX

VIN = Vo + 5V,
10 = lA

30

45/60

50/60

30

45/60

50/60

mAMAX

10 Hz - 100 kHz,
10 = 5mA

150

7001700

240

1000/1000

""Vrms

Ripple Rejection fo = 120 Hz, 1 Vrms•
10 = 100mA
LM2940
LM2940C
fo
10

72
72

60/54
60

66

= 1 kHz. 1 Vrms•
= 5mA

Long Term
Stability

10

= lA
= 100mA

dBMIN
dBMIN
54/48

60/50
20

Dropout Voltage 10

54/48

dBMIN

mVI

32

1000 Hr

0.5

0.8/1.0

0.711.0

0.5

0.8/1.0

0.7/1.0

VMAX

110

150/200

150/200

110

150/200

150/200

mVMAX

2-55

•

Electrical Characteristics (Continued)
VIN = Vo + 5V, 10 = 1A, Co = 22 ",F, unless otherwise specified. Boldface limits apply over the entire operating
temperature range of the Indicated devIce. All other specifications apply for TA = TJ = 25°C.
Output Voltage (Vo)

Parameter

Conditions

5V

8V

LM2940T-5.0
LM2940K-5.0/883
LM2940T-8.0 LM2940K-8.0/883
LM2940CT-5.0
Typ
Limit
Limit
Limit
Limit
Typ
Units
(Note 6)
(Note 5)
(Note 6)
(Note 5)
6.25V';;: VIN ,;;: 26V

Short Circuit
Current

(Note 7)

Maximum Line
Transient

Ro = 1000
LM2940, T ,;;: 100 ms
LM2940/883, T ,;;: 20 ms
LM2940C, T ,;;: 1 ms

Reverse Polarity Ro = 1000
DC Input Voltage LM2940, LM2940/883
LM2940C

1.9

1.6

75

60/60

1.5/1_3

9.4V ,;;: VIN ,;;: 26V
1.9

1.6

75

60/60

40/40
55

45

-30
-30

-15/-15
-15

Reverse Polarity Ro = 1000
-75
Transient Input LM2940, T ,;;: 100 ms
LM2940/883, T ,;;: 20 ms
Voltage
LM2940C, T ,;;: 1 rns
-55

-15/-15

-50/-50
-45/-45
-45/-45

2-56

-30

-15/-15

-75

-50/-50

1.6/1.3

AMIN

40/40

VMIN
VMIN
VMIN

-15/-15

-45/-45

VMIN
VMIN
VMIN
VMIN
VMIN

Electrical Characteristics

(Continued)
VIN = Vo + 5V, 10 = 1A, Co = 22 ""F, unless otherwise specified. Boldface limits apply over the entire operating
temperature range of the Indicated device. All other specifications apply for TA = TJ = 25'C.
Output Voltage (Vo)

Parameter

9V

Conditions

Typ
10.5V

s:

Output Voltage

5 mA

Line Regulation

Vo + 2V s: VIN
10 = 5mA

Load Regulation

50mA

Output Impedance

100mADCand
20mArms,
fo = 120 Hz

Quiescent
Current

10 S:1A

s:

10

s:

s: 2BV,

1A

Vo +2V s: VIN
10=5mA

s: VIN s:

Units

26V

10.00

9.70/9.50
10.30/10.10

VMIN
VMAX

20

90

20

100

mVMAX

60

90/110

65

100/181

mVMAX

60

< 2BV,

11.5V

LM2940T·10
Limit
(Note 5)

B.73/8.55
9.27/9.45

mO

65

10

15/20

10

15/20

mAMAX

45/80

30

45/80

mAMAX·

VIN = Vo + 5V, 10 = 1A

30

10 Hz - 100 kHz,
10 = 5mA

270

Ripple Relectlon

fO = 120 Hz, 1 Vrms ,
10=100mA

84

Dropout Voltage

s: VIN s: 26V

Typ

9.00

Output Noise
Voltage

Long Term
Stability

10V

LM2940T·9.0
Limit
(Note 5)

300

52/48

B3

""Vrms
51/41

mVl
1000 Hr

36

34

dBMIN

10 = 1A

0.5

0.B/1.0

0.5

0.B/1.0

VMAX

10 = 100 mA

110

150/200

110

150/200

mVMAX

1.9

1.6

1.9

1.B

AMIN

75

BO/80

75

60/80

VMIN

-30

-15/-18

-30

-15/-15

VMIN

-75

-50/-50

-75

-50/-50

VMIN

Short Circuit
Current

(Note 7)

Maximum Line
Transient

Ro = 1000
T s: 100ms

Reverse Polarity
DC Input Voltage

RO = 1000

Reverse Polarity
Transient Input
Voltage

Ro = 1000
T s: 100ms

2·57

Electrical Characteristics

(Continued)
VIN = Vo + 5V, 10 = 1A, Co = 22 p.F, unless otherwise specified. Boldface limits apply over the entire operating
temperature range of the indicated device. All other specifications apply for TA = TJ = 25°C.
Output Voltage (Vo)

Parameter

Conditions

12V

15V

LM2940T·12
LM2940K·12/883
LM2940CT-15 LM2940K-15/88.
LM2940CT-12.C
Typ
Typ
Limit
Limit
Limit
Limit
Units
(Note 6)
(Note 5)
(Note 6)
(Note 5)
16.75V ,;: Y,N ,;: 26V

13.6V ,;: Y,N ,;: 26V
Output Voltage

5mA,;:lo';:1A

Line Regulation

Vo + 2V ,;: VIN ,;: 26V,
10 = 5mA

Load Regulation

50 mA,;: 10';: 1A
LM2940, LM2940/8.8.3
LM2940C

Output Impedance 100mADCand
20mArms,
fo=120Hz
Quiescent
Current

Vo +2V,;: VIN ,;: 26V,
10=5mA
LM2940, LM2940/883
LM2940C

12.00 11.64/11.40
12.36/12.60
20

120

75/120

55
55

120/200
120

120/190

1000/1000

8.0

15/20
15

15/20

VIN = Vo + 5V, 10 = 1A 30

45/60

10 Hz - 100 kHz,
10=5mA

Ripple Rejection

fo = 120 Hz, 1 Vrms ,
10=100mA
LM2940
LM2940C

360

66
66

150

100

15

50/60

30

45/60

1000/1000

450

64

14.55/14.25
15.45/15.75

VMIN
VMAX

95/150

mVMAX

150/240

mVMAX
mVMAX

1000/1000

mO

15/20

mAMAX
mAMAX

50/60

mAMAX

1000/1000

p.Vrms

dBMIN
dBMIN

52

52/46

48/42

dBMIN
mV/
1000 Hr

60

48
10= 1A

0.5

0.8./1.0

0.7/1.0

0.5

0.8./1.0

0.7/1.0

VMAX

10 = 100mA

110

150/200

150/200

110

150/200

150/200

mVMAX

1.9

1.6

1.6/1.3

1.9

1.6

1.6/1.3

AMIN

75

60/60
40/40

VMIN
VMIN
VMIN

Short Circuit
Current

(Note 7)

Maximum Line
Transient

Ro = 1000
LM2940, T ,;: 100 ms
LM2940/883, T ,;: 20 ms
LM2940C, T ,;: 1 ms

Reverse Polarity Ro = 1000
DC Input Voltage LM2940, LM2940/883
LM2940C
Reverse Polarity
Transient Input
Voltage

20

10

54/48
54

fo = 1 kHz, 1 Vrms,
10 = 5mA
Long Term
Stability

15.00 14.55/14.25
15.45/15.75

70

10
10

Output Noise
Voltage

Dropout Voltage

11.64/11.40
12.36/12.60

40/40
55

45

-30
-30

-15/-15
-15

Ro = 1000
-75
LM2940, T ,;: 100 ms
LM2940/883, T ,;: 20 ms
LM2940C, T ,;: 1 ms
-55

55

45

-30

-15

-15/-15

-15/-15

-50/-&0
-45/-45
-45/-45

2-58

-45/-45
-55

-45/-45

VMIN
VMIN
VMIN
VMIN
VMIN

Note 1: Absolute Maximum Ratings are limits beyond which damage to the device may occur. Operating Conditions are conditions under which the device
functions but the specifications might not be guaranteed. For guaranteed specifications and test conditions see the Electrical Characteristics.

Note 2: Military specifications complied with RETS/SMD at the time of printing. For current specifications refer to RETS LM2940K-5.0, LM2940K-8.0, LM2940K-12,
and LM2940K-15. SMD numbers are 5962-8958701YA(5V), 5962-9083301YA(8V), 5962-9088401YA(12V), and 5962-908850IYA(15V).
Note 3: The maximum power dissipation is a function of the maximum junction temperature, T J

=

150°C, the junction-to-ambient thermal resistance. (J JA. and the

ambient temperature, TA. The maximum allowable power dissipation at any ambient temperature is PDMAX ~ (150 - TA)/8JA.lf this dissipation is exceeded, the
die temperature will rise above 150'C and the LM2940 will go into thermal shutdown. For the LM2940T and LM2940CT, the junction-to-ambient thermal resistance
(OJA) is 53'C/W. When using a heatsink, OJA is the sum of the 3'C/W junction-to-case thermal resistance (8Je) of the LM2940T or LM2940CT and the case-te-am-

bient thermal resistance of the heatsink. For the LM2940K, 8JA is 39 C/W and 8JC is 4°C/W.
D

Note 4: ESD rating is based on the human body model, 100 pF discharged through 1.5 ka.
Note 5: All limits are guaranteed at TA ~ TJ ~ 25'C only (standard typeface) or over the entire operating temperature range of the indicated device (boldface
type). All limits at TA ~ TJ ~ 25'C are 100% production tested. All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality
Control methods.
Note 6: All limits are guaranteed at TA ~ TJ ~ 25'C only (standard typeface) or over the entire operating temperature range of the indicated device (boldface
type). All limits are 100% production tested and are used to calculate Outgoing Quality Levels.
Note 7: Output current will decrease with increasing temperature but will not drop below 1A at the maximum specified temperature.

Ell

2-59

Typical Performance Characteristics
Dropout Voltage
vs Temperature

Dropout Voltage
0.9

~

0.8

~

0.7

m
s
5

1.0

TJ ' 25°C

~

0.8

.,

0.5
0.4

!;

0.3

~

0.2

~

i"

....

Q

o/
o

~

5.10
5.08

0.9
0.8
0.7
0.8

I - -!:i

S!

SOOm 1000--

... ~

400

100

800

o

1000

40

r-- rl'N -

i"

....

...

I

i

500 mA
10m

10

I

o

-40

40

80

120

~~
~

.5
3V

''is

9~

OV
-10 0

10

20

30

40

50

X

0.5
0.4
0.3

10

I!IN' 10~IB.
5.00 COUTo 221'F
2.00 Ig'SOmA
Vo =5V
1.00
0.50
0.20

5

0.10

I!:
6

20

25

30

35

0

_io""

0.2

~
zQ

;:::

~

55
45

o

35
30

40

1

~

o

-

100

lk

10k lOOk 1M

Maximum Power
Dissipation (T()"3)
~
~

r--

10

FREQUENCY (Hz)

INFINITE HEAT SINK

0.02
0.01 UJJUUlLJ.I.IIIILllllllL.LlJIIULlJUIIIL.llllII
1
10 100 lk 10k lOOk 1M

~

Yo '5Y

as

0.5

;

0.05

!1il

75

i!

22
20
lB
18
14
12
10

1.0

~u;~~;~F
as 19- IOm

s
.:s

-0.1
-0.2
-0.3
-0.4
-0.5
1.0

20

0.8

Ripple ReJection

IN-l~!

10

0.8

15

r-- r- COUT"22/'F
1~ -TJ "250C
D.2
0.1 f:= '-- vo" 5Y
0

0

0.4

LOAD CURRENT (A)

Maximum Power
DI88lpatlon (TO-220)

if

FREQUENCY (Hz)

15

TIME (1")

10.00

e~

-...

10
0

1--!_

Output Impedance

i!

r 50 mA

1A

TIME (1'.)

g

20

r lOOm

40
20

-- r-I- VV,oH"4V
.5V ;-r-~
-- !- t- TJ' 250C ...,~~

30

100
80
80

-10

80

180

I

r\

120

Losd Transient Response

i
5~
§Q

It

120

L

INPUT VOLTAGE (v)

~~

80

Quiescent Current
40

180
140

Line Transient Reeponse

~I

40

TEMPERATURE (OC)

180

o
o

180

-

50

TEMPERATURE (OC)

i~

-40

180

Quiescent Current

1
1

20

120

200

V

40
30

80

TEMPERATURE (OC)

Quiescent Current
vs Temperature
o.

-I-

4.90
-40

OUTPUT CURRENT (mA)

50

8

--

100niA

0.1

200

1A

0.5
0.4
0.3
0.2

""",io""

0.1

Output Voltage
vs Temperature

10oC/W HEAT SINK

'"'!'--.I.
1'10..
NO HEAT SINK

o 10 20 30 40 50 80 70 80 90100
AMBIENT TEMPERATURE (oC)

I
i

22
20
18
18
14
12
10

INFINITE HEAT SINK

I'

....

10oC/W HEAT SINK

'"'!'--.I.

o

,....

NO HEAT SINK

o 10 20 30 40 50 80 70 80 90100
AMBIENT TEMPERATURE (OC/W)

TUH/8822-4

2·60

Typical Performance Characteristics
Low Voltage Behavior
5.0

E

~~

3.0

=>

5
0

V

/

2.0

1.0

2.0

E

V

/

TJ

12

Vo

10

= fA
= 25°C
= BY

~

5.0

!I

o

10 =

E

~~

Vo

1A

J

1/

0

o

E

/

10

10

15

I.

16

~

~~

~~

20

30

E

~

12

/

/

I

o

6

12

16

~
w

5l

1\.1= l~on
Va = 9V

12

~

~

I
I
0

I
II

~

~
2:

10

20

30

-4
-30 -20 -10

40

0

10

20

INPUT VOLTAGE (v)

Output at
Voltage Extremes

Output at
Voltage Extremes

Output at
Voltage Extremes

20
16

15
10

~~

L

~

~
-5
-30 -20 -10

0

10

25

1\.1= l~on
Va = 12V

20

~

12

w

5l
~

;c

§

20

INPUT VOLTAGE (V)

30

40

~

I

~

II

18

Output at
Voltage Extremes
20

INPUT VOLTAGE (V)

~

15

INPUT VOLTAGE (v)

INPUT VOLTAGE (V)

1\.1= lJon
Vo = 10V

lB

/

14

12

-4
-30 -20 -10

40

25
20

10

1\.1= l~on
Vo = BV

5
10

B

15

/

!5

o

0

0

~

5
6

!5

I

~

~

Output at
Voltage Extremes
20

~

~

0

4

12

J

10 = lA
15 TJ = 25°C
Va = 15V
12

INPUT VOLTAGE (V)

1\.1 = I~On
Vo = 5V

-2
-30 -20 -10

/

/
o
o

9

Low Voltage Behavior

/

Output at
Voltage Extremes

E

6

INPUT VOLTAGE (V)

/

2:

12

o

14

/

~

6

12

I.

~~

INPUT VOLTAGE (v)

12

10

'0 = lA
TJ = 25°C
Vo = 12V

12

(

o

o
4

Low Voltage Behavior
14

= 25°C
= IOV

~

/
(

INPUT VOLTAGE (V)

12

~

/

§

/

6.0

= fA

15 TJ = 25°C
Va = 9V
12

~

/

5
4.0

~~

/

Low Voltage Behavior
15 TJ

E

>

INPUT VOLTAGE (V)

I.

10

0

!5

o
3.0

Low Voltage Behavior
lB

w

0

I

1.0

10

/V

TJ = 25°C
Vo = 5V

4.0

Low Voltage Behavior
14

10 = lA

(Continued)

-4
-30 -20 -10

0

15

10

20

30

40

30

40

1/

10

I

§

INPUT VOLTAGE (V)

40

1\.1= l~on
Va = 15V

!5

II

30

1/
-5
-30 -20 -10

0

10

20

INPUT VOLTAGE (v)

TLlH/8822-5

2-61

Typical Performance Characteristics (Continued)

:s

100 Output Capacitor ESR

3.0

Caul = 22 p.F
Va
5V

Peak Output Current

=

10~--+---~---+---4--~

:5
...
15

..... i'.

2.0

V,N =14V

""

""""
<.>

:::>

...

~ 1.0
is

o

0.01'----"'----'----'-----'-----'
o 200 400 600 800 1000

-40

OUTPUT CURRENT (rnA)

o

40

80

120

160

TEMPERATURE (OC)
TL/H/BB22-6

TL/H/B622-B

Typical Application
Your

ViN
UNREGUlATED
INPUT

REGUlATED
OUTPUT

Al¢J

J22¢

Cl·

Cour··

TL/H/6822-3

'Required H regulator is located far from power supply filter.
"CoUT must be at least 22 p.F \0 maintain stability. May be increased without bound to maintain regulation during transients. Locate as close as possible \0 the
regulator. This capacitor must be rated over the same operating temperature range as the regulator and the ESR is critical; see curve.

Connection Diagram
(TO-220) Plastic Package

TO-3 Metal Can Package (K)

TL/H/6622-2

Front View
Order Number LM2940T-5.0, LM2940T-S.O,
LM2940T-9.0, LM2940T-10, LM2940T-12,
LM2940CT-5.0, LM2940CT-12 or LM2940CT-15
See NS Package Number T03B

TLlH/8B22-7

Bottom View
Order Number LM2940K-5.0/SS3,
LM2940K-S.O/SB3, LM2940K-121BB3, LM2940K-15/SB3
See NS Package Number K02A

2·62

~National

~ Semiconductor

LM2941/LM2941C 1A Low Dropout Adjustable Regulator
General Description
The LM2941 positive voltage regulator features the ability to
source 1A of output current with a typical dropout voltage of
O.SV and a maximum of 1V over the entire temperature
range. Furthermore, a quiescent current reduction circuit
has been included which reduces the ground pin current
when the differential between the input voltage and the output voltage exceeds approximately 3V. The quiescent current with 1A of output current and an input-output differential of SV is therefore only 30 mA. Higher quiescent currents
only exist when the regulator is in the dropout mode (VIN Your s: 3V).
Designed also for vehicular applications, the LM2941 and
all regulated Circuitry are protected from reverse battery installations or two-battery jumps. During line transients, such
as load dump when the input voltage can momentarily exceed the specified maximum operating voltage, the regu-

lator will automatically shut down to protect both the internal
circuits and the load. Familiar regulator features such as
short circuit and thermal overload protection are also provided.

Features
•
•
•
•
•
•
•

Output voltage adjustable from SV to 20V
Dropout voltage typically O.SV @ 10 = 1A
Output current in excess of 1A
Trimmed reference voltage
Reverse battery protection
Internal short circuit current limit
Mirror image insertion protection
II P+ Product Enhancement tested
• TTL, CMOS compatible ON/OFF switch

Equivalent Schematic and Connection Diagram
r---r--------------------------1>----t----1DVIN

r--....,..--I-....;::..--I--+--_-+--I-<~]VOUT

H--+"""+--+--+--DADJ

L-~----~~~--~~~--~~--~----~--~--~+_-~

____+_~GND

L---------------------------------lDON/OFF
TL/H/8823-1

Connection Diagram and Ordering Information
4-Lead TO-3 (K)

(10-220)
Plastic Package

GrO~nd
0
Output

C... I. +VIN

Oli/OFF

0

:~

Ad)

ADJUST

TL/H/8823-7

TL/H/8823-2

Bottom View

Front View

Order Number LM2941K/883
See NS Package Number K04A

Order Number LM2941T or LM2941CT
See NS Package Number T05A
2-63

o
....
;J;
N

:&

.....
....

....I

~

:&
....I

Lead Temperature (Soldering, 10 seconds)
TO-3 (K) Package
TO-220 (T) Package
ESD susceptibility to be determined.

Absolute Maximum Ratings

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications•
Input Voltage (Survival Voltage, :5: 100 ms)
LM2941 K, LM2941 T
SOV
LM2941CT
45V
Internal Power Dissipation (Note 3)
Internally Limited
Maximum Junction Temperature
150'C
Storage Temperature Range

-S5'C :5: TJ :5:

300"C
2SO"C

Operating Ratings
Maximum Input Voltage
Temperature Range
LM2941K
LM2941T
LM2941CT

+ 150'C

2SV
-55'C :5: TJ :5: 150'C
-40'C:5: TJ :5: 125'C
-O'C :5: TJ :5: 125'C

Electrical Characteristics-LM2941 K, LM2941T

5V :5: Vo :5: 20V, VIN = Vo + 5V, Co = 22 ,...F, unless otherwise specified. Specifications in standard typeface apply for TJ =
25'C, while those in boldface type apply over the full Operating Temperature Range.
Parameter

Conditions

Reference Voltage

5 mA,;; 10';; 1A (Note S)

Line Regulation

Vo

+ 2V :5: VIN

:5: 2SV, 10 = 5 mA

Typ

LM2941K
Umlt
(Notes 2, 4)

LM2941T
Umlt
(Note 5)

Units
(Umits)

1.275

1.237/1.211
1.313/1.339

1.237/1.211
1.313/1.339

V(min)
V(max)

4

10/10

10/10

mVIV(max)

10/10

10/10

mV/V(max)

Load Regulation

50mA:5: 10:5: 1A

7

Output Impedance

100 mADC and 20 mArms
fo = 120 Hz

7

Quiescent Current

Vo

+ 2V :5: VIN < 2SV, 10 =
+ 5V, 10 = 1A

5 mA

VIN = Vo

10

15/20

15/20

mA(max)

30

45/60

45/60

mA(max)

RMS Output Noise,
% ofVOUT

10 Hz-100 kHz
10 = 5mA

0.003

Ripple Rejection

fo = 120 Hz, 1 Vrms, IL = 100 mA

0.005

Long Term Stability

mOIV

%
0.02/0.04

0.02/0.04

0.4

%/V(max)
%/1000 Hr

10 = 1A

0.5

0.8/1.0

0.8/1.0

V(max)

10=100mA

110

200/200

200/200

mV(max)

Short Circuit Current

VIN max = 2SV (Note 7)

1.9

I.S/1.3

1.S

A(min)

Maximum Line
Transient

Vo max tV above nominal Vo
Ro = 1000, T :5: 100 ms

75

SO/60

SO/60

V(min)

31

26/26

26/26

Voc

-30

-15/-1S

-15/-1S

V(min)

-75

-50/-50

-50/-50

V(min)

1.30

0.80/0.80

0.80/0.80

V(max)

1.30

2.00/2.00

2.00/2.00

V(min)

50

100/300

100/300

,...A(max)

Dropout Voltage

Maximum Operational
Input Voltage
~

Reverse Polarity
DC Input Voltage

Ro = 1000, Vo

Reverse Polarity
Transient Input Voltage

T:5: 100 ms, Ro = 1000

ON/OFF
Threshold Voltage
ON

10:5: 1A

ON/OFF
Threshold Voltage
OFF

10:5: 1A

ON/OFF
Threshold Current

VON/OFF = 2.0V,
10:5: lA

-O.SV

2-64

Electrical Characteristics-LM2941 CT

5V ,;;: Vo ,;;: 20V, VIN = Vo + 5V, Co = 22 ,...F, unless otherwise specified. Specifications in standard typeface apply for TJ =
25'C, while those in boldface type apply over the full Operating Temperature Range.
Parameter
Reference Voltage

Typ

Conditions
5mA,;;: 10';;: 1A(Note6)

+ 2V ,;;: VIN

1.275

Limit
(Note 5)

Units
(Limits)

1.23711.211
1.313/1.339

V(min)
V(max)

Line Regulation

Vo

4

10

mVIV(max)

Load Regulation

50 mA,;;: 10';;: lA

7

10

mVIV(max)

Output Impedance

100 mADC and 20 mArms
fo=120Hz

7

Quiescent Current

Vo

,;;: 26V, 10 = 5 mA

+ 2V ,;;: VIN < 26V, 10 =
+ 5V,lo = 1A

5 mA

VIN = Vo
RMS Output Noise,

10

15

mA(max)

30

45/60

mA(max)

% OfVOUT

10Hz-100kHz
10 = 5mA

0.003

Ripple Rejection

fo = 120 Hz, 1 Vrms, IL = 100 mA

0.005

Long Term Stability
Dropout Voltage

mOIV

%
0.02

%1V(max)
%/1000 Hr

0.4
10 = 1A

0.5

0.B/1.0

V(max)

10 = 100mA

110

200/200

mV(max)

Short Circuit Current

VIN max = 26V (Note 7)

1.9

1.6

A(min)

Maximum Line
Transient

Vo max 1 V above nominal Vo
Ro = 1000, T,;;: 100 ms

55

45

V(min)

31

26

Voe

-30

-15

V(min)

-55

-45

V(min)

1.30

O.BO

V(max)

1.30

2.00

V(min)

50

100

,...A(max)

Maximum Operational
Input Voltage
Reverse Polarity
DC Input Voltage

Ro = 1000, Vo:2: -O.SV

Reverse Polarity
Transient Input Voltage

T,;;: 100 ms, Ro = 1000

ON/OFF
Threshold Voltage
ON

10';;: 1A

ON/OFF
Threshold Voltage
OFF

10';;: 1A

ON/OFF
Threshold Current

VON/OFF = 2.0V,
10';;: 1A

Note 1: Absolute Maximum Ratings Indicate limits beyond which damage to the davies may occur. Operating ratings Indicate conditions for which the device Is
Intended to be functional, but davlce parameter specifications may not be guaranteed under these conditions. For guaranteed specifications and test conditions,
see the Electrical Characteristics.
Note 2: A military RETS specification available upon request. At the time of printing, the LM2941 1883 RETS specification complied with the boldface limits In this
column. The LM2941 K/883 may also be procured to a Standard MIlitary Drawing.
Note 3: The maximum power dissipation Is a function of TJ(max). 8JA, and TA. The maximum allowable power dissipation at any ambient temperature Is Po =
(TJ(max) - TA)/8JA.lfthls dissipation Is exceeded, the die temperature will rise above 150'C and the LM2941 will go Into thermal shutdown. For the LM2941T and
LM2941CT, the Junctlon·to·amblent thermal resistance (8JAlls 53'C/W, and the Junctlon·to.case thermal resistance (8Jc) Is 3'C/W. For the LM2941K, 8JA Is
35'C/W and 8JC Is 4'C/W.
Note 4: All limits guaranteed at room temperature (standard typeface) and at temperature extremes (boldface type). All limits are used to calculate Outgoing
Quality Level, and are 100% production tested.
Note 5: All limits guaranteed at room temperature (standard typeface) and at temperature extremes (boldfaes type). All room temperature limits are 100%
production tested. All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods.
Note 6: The output voltage range Is 5V to 20V and Is determined by the two external resistors, Rl and R2. See Typical Application Circuit.
Note 7: Output current capability will decrease with Increasing temperature, but will not go below 1A at the maximum specified temperatures.

2·65

•

Typical Performance Characteristics
Dropout Voltage vs
Temperature

Dropout Voltage
0.9

E
~

~

0.8
0.7

0.5

~
~

o.~

~
~

0.9

5.08

0.8

5.06

_....

1/

o
o

0.4
0.3

~

.....

0.2

-

0.5

i-""

0.3

O.

5.10

0.6

V

-I-

0.2
O. I

-

400

600

800

1000

50

30

il1

40

15

20

~

10

ti

":?

I-

-S

i

SOOmA

-

'-- r-r
lOrnA

40

80

1\

\

100
80

ti

60

120

~;:

~~
go

Vo=.E..

"'SO
;!i~
g~

-

~;

~~

3:
3V

IIA I

x
o

10

o~

~il1

S

OV

0.5
0.4
0.3
0.2
0.1
0
-0.1
-0.2
-0.3
-0.4
-0.5
1.0

rrr-

r-

_
_
_
-

30

40

50

60

~

0.20
0.10

iiiQ

..
e;

0.02
10

100

Ik

10k lOOk

FREQUENCY (Hz)

0.2

1M

0.4

0.6

0.8

1.0

LOAD CURRENT (A)

Ripple Rejection
95

VIN = 10~ Ig_
CaUT = 22 pF
85 IO=10mA
Vo =5V
75

1~~

'"
3
z

65
55
45

o
10

20
18
16
14
12
10
8

20

30

40

10

22

:g

~
10oC/W HEAT SINK

"'i--.
r-Io..

o
o

Ik

10k lOOk

1M

Maximum Power
Dissipation (TO-3)
I\.

---

100

FREQUENCY (Hz)

INFINITE HEAT SINK

NO HEAT SINK

2

0.0 I

,/

.....

o
o

35

t- '-r-

.... 1-

10

.~

~

0.05

160

1....-

20

~

22

0.50

O!

~

30

Vo=5V

Maximum Power
Dissipation (TO-220)

~

120

TJ = 25°C r- -r-

TIME (p.)

VIN = 10~ III.
5.00 CaUT = 22 pF
1a=50mA
2.00
Vo =5V
1.00

5

30

iil

-10

10.00

~

25

0.5

Output Impedance

i

20

VIN=IOV
CaUT=22pF
TJ =25 OC
VO=5V

TIME (ps)

:s

IS

r500mA

(§is

20

iS

Load Transient Response

..
0

10

40

INPUT VOLTAGE (V)

-10
-20
-30

-10 0

":?

~~

rlOOmA

40

160

80

Quiescent Current

""\

120

o

'\

>0

40

TEMPERATURE (DC)

-S

20

Line Transient Response

Oz

-40

160

VIN = 14V

TEMPERATURE (DC)

~'>
!:;..5

120

VO=5V

140

z

I

-40

80

50

160

~

~

I

o

30
20
10

~.9~

4.92

Quiescent Current
180

--

S

4.96

200

IA

-I-'"

4.98

TEMPERATURE (DC)

VIN = 14V
Vo =5V

'--r-

15

-S

5.00

~

I
100mA.

,---

5.02

~
~

500m .....

Vo=5V

4.90
-40

Quiescent Current vs
Temperature

~O

~~

IA

- , - r-

5.04

o
200

OUTPUT CURRENT (mA)

":?

Output Voltage

1.0

0.7

o.s

I::
Q

TJ = 25°

~

INFINITE HEAT SINK

20
18
16
I~

12
10

---

i

AM81ENT TEMPERATURE (DC)

N--.

-""-r-f-.

2

o
10 20 30 40 50 60 70 80 90100

10oC/W HEAT SINK

NO HEAT SINK

o 10 20 30 40 50 60 70 80 90100
AMBIENT TEMPERATURE (OC/W)
TLIHI8823-4

2-66

Typical Performance Characteristics
Low Voltage Behavior
5.0

E

4.0

10 lA
TJ ~ 25'C
Vo ~ 5V

Low Voltage Behavior
18

V

15

E

.

V
1.
~V

~

!:;

g 3.0

c~

~

2.0

1.0

1.0

2.0

I

III

12

....'">
~
§

4.0

5.0

/

E
...
'"
!:l
....'">

.

III
~
~

11

20

~

~

~

I

o

18

200

.coo

600

800
OUTPUT CURRENT (mA)

1000

Peak Output Current
3.0

R[=IJOIl

I- Vo =15V

3:

15

VIJ .l4V
Vo =5V

G

J

~

II

1.0

o

-5
-30 -20 -10 0

"

~ 2.0

1/

10

~
'"

w

STA8LE
REGION

... 0.0 1

9 12 15
INPUT VOLTAGE (V)
6

:0

0
m
INPUT VOLTAGE (V)

I

1

§ o.1~
:!l

25

RL=100!1
VO=5V

-~-m-w

10

Output at
Voltage Extremes

E

-2

CoUT = 22/,F
Vo=5V

is

3

Output at
Voltage Extremes

100

III

/

6.0

12

'"

lL

I

lL

t

3.0

....
~
:0

Output Capacitor ESR

g

10 ~ lA I
TJ = 25'C
Vo ~ 15V

!:l

INPUT VOLTAGE IV)

10

(Continued)

10 20 3D
INPUT VOLTAGE (V)

40

0
-40

0

40

80

120

160

TEMPERATURE (oc)
TUH/BB23-5

Definition of Terms
Dropout Voltage: The input-voltage differential at which
the circuit ceases to regulate against further reduction in
input voltage. Measured when the output voltage has
dropped 100 mV from the nominal value obtained at (Vour
+ 5V) input, dropout voltage is dependent upon load current and junction temperature.
Input Voltage: The DC voltage applied to the input terminals with respect to ground.

Load Regulation: The change in output voltage for a
change in load current at constant chip temperature.
Long Term Stability: Output voltage stability under accelerated life-test conditions after 1000 hours with maximum
rated voltage and junction temperature.
Output Noise Voltage: The rms AC voltage at the output,
with constant load and no input ripple, measured over a
specified frequency range.

Input-Output Differential: The voltage difference between
the unregulated input voltage and the regulated output voltage for which the regulator will operate.
Line Regulation: The change in output voltage for a
change in the input Voltage. The measurement is made under conditions of low dissipation or by using pulse techniques such that the average chip temperature is not significantly affected.

Quiescent Current: That part of the positive input current
that does not contribute to the positive load current. The
regulator ground lead current.
Ripple Rejection: The ratio of the peak-to-peak input ripple
voltage to the peak-to-peak output ripple voltage.
Temperature Stability of Vo: The percentage change in
output voltage for a thermal variation from room temperature to either temperature extreme.

2-67

fII

or-----------------------------------------------------------------------,
...
~

Typical Applications

~
.....

5V to 20V Adjustable Regulator

...
~

~

r

+-__+--o

- _ . L1
:;,;N_1!!!!!!_ _

OFF
tON/OFF

~

OUT

VOUT
5V to 20V
01A

R2
LM2941

ADJ

ON
Rl

GND

TL/H/BB23-3

Vour

AI + A2

'Aequlred If regulator Is located far from power supply filter.
"COUT must be at least 22 I'F to maintain stability. May be Increased without bound to maintain regulation during transients. Locate as close as possible to the regulator. This capacRor must be rated over the same operating
temperature range as the regulator and the ESA Is critical; see curve.

= Aeferencevoltage x -A-I-whereVREF = 1.275 typical

Solvin9 for R2: A2

= AI

(V~~F -

I)

Note: Using Ik for AI will ensure thal the Input bias current error of the
adjust pin will be negligible. Do not bypass AI or A2. This will lead to Instabil-

Ities.

1ASwltch
12V

y.
liN

R3
33kn.·..

OUT

ON/OFF

l

OFF

51

:k ~~IN4001 ~II
- -::- .Lt

LW2941

ON

,J;.ND

,2J1.F

). LOAD

~DJ
TL/H/BB23-8

"'To assure shutdown, select Aeslstor A3 to guarantee at least 300 I'A of pull-up current when 81 Is open. (Assume 2V at the ON/OFF pin.)

2·68

.-------------------------------------------------------------------------,r
iii:

~National

N

CD
CO

~ Semiconductor

.j:Io

LM2984 Microprocessor Power Supply System
General Description
The LM2984 positive voltage regulator features three independent and tracking outputs capable of delivering the power for logic circuits, peripheral sensors and standby memory
in a typical microprocessor system. The LM2984 includes
circuitry which monitors both its own high-current output and
also an external p.P. If any error conditions are sensed in
either, a reset error flag is set and maintained until the malfunction terminates. Since these functions are included in
the same package with the three regulators, a great saving
in board space can be realized in the typical microprocessor
system. The LM2984 also features very low dropout voltages on each of its three regulator outputs (0.6V at the rated output current). Furthermore, the quiescent current can
be reduced to 1 mA in the standby mode.
Designed also for vehicular applications, the LM2984 and
all regulated circuitry are protected from reverse battery installations or 2-battery jumps. Familiar regulator features
such as short circuit and thermal overload protection are

also provided. Fixed outputs of 5V are available in the plastic TO-220 power package.

Features
•
•
•
•
•
•
•
•
•
•
•
•
•
•

Three low dropout tracking regulators
Output current in excess of 500 mA
Fully specified for -40·C to + 125·C operation
Low quiescent current standby regulator
Microprocessor malfunction RESET flag
Delayed RESET on power-up
Accurate pretrimmed 5V outputs
Reverse battery protection
Overvoltage protection
Reverse transient protection
Short Circuit protection
Internal thermal overload protection
ON/OFF switch for high current outputs
P+ Product Enhancement tested

Typical Application Circuit
5V

r:t-

RHST

1pF

I;/;
5V.500mA

1 1 r - - - - -..... ; . . . - - - -.. 10

I-I--...-....;,~ VOUT

VBUFFER

-h+ 10 pF
];

5V.l00mA

a-;.;.-"'---i

r

'+
...l±.10pF

LM29S4

PERIPHERAL
SENSORS

•

MONITOR OUT HI-----~ PPMON
RESET IN

RESET

RT

STANDBY
MEMORY

5V. 5 mA

Order Number LM2984T
See NS Package Number TA118

CoUT must be at least 10 "F to
maintain stability. May be increased
without bound to maintain regulation
during transients. Locata as close as
possible to the regulator. This capac- TLlH/11252-1
itor must be rated over the same op·
erating temperature range as the
regulator. The equivalent series re-

sistance (ESR) of this capacitor is
critical; see curve.

2-69

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
input Voltage
Survival Voltage « 100 ms)
Operational Voltage

Internal Power Dissipation

60V
26V

Internally Limited

Operating Temperature Range (TA)
-40'Cto
Maximum Junction Temperature (Note 1)

+ 125'C

Storage Temperature Range
Lead Temperature (Soldering, 10 sec.)
ESD Susceptability (Note 3)

+ 150'C

-65'Cto

150'C
230'C
2000V

Electrical Characteristics
VIN = 14V, lOUT = 5 mA, COUT = 10 ,..F, unless otherwise indicated. Boldface type refers to limits over the entire operating
temperature range, -40'C s: TA s: + 125'C, all other limits are for TA := Tj = 25'C (Note 6).
Typical

Limit
(Note 2)

Units

5.00

4.85/4.75
5.15/5.25

Vmin
Vmax

VIN

2

25/25

mVmax

VIN

5

50/50

mV max

12

50/50

mVmax

Parameter

Conditions

VOUT (Pin 11)
Output Voltage
Line Regulation

5 mA s: 10 s: 500 rnA
6V s: VIN s: 26V

s: 16V
s: 26V
5 mA s: lOUT s: 500 mA
9V

7V
Load Regulation
Output Impedance
Quiescent Current

s:
s:

250 mAcJc and 10 mArms ,
fo = 120Hz
lOUT
lOUT

Output Noise Voltage

=
=

mO

24

500mA

38

100/100

mAmax

250mA

14

50/50

mAmax

10 Hz-100 kHz, lOUT

=

100 mA

100

Long Term Stability

,..V

20

=

Ripple Rejection

fo

Dropout Voltage

lOUT
lOUT

=
=

60/50

dBmin

500mA

0.53

0.80/1.1

V max

250mA

0.28

0.50/0.70

Vmax

0.92

0.75/0.60

Amln

32

26/26

Vmin

65

60/60

Vmin

-30

-15/-15

Vmin

-55

-35/-35

Vmin

Current Limit
Maximum Operational
Input Voltage

Continuous DC

s:

=

Maximum Line Transient

VOUT

Reverse Polarity
Input Voltage DC

VOUT ~ -0.6V, ROUT

Reverse Polarity Input
Voltage Transient

T

s:

mVl1000 hr

70

120 Hz

6V, ROUT

100 ms. ROUT

=

1000, T

=

s:

100 ms

1000

1000

2·70

Electrical Characteristics (Continued)
VIN = 14V, Ibuf = 5 mA, Cbuf = 10 f.£F, unless otherwise indicated. Boldface type refers to limits over the entire operating
temperature range, -40'C :S: T A :S: + 125'C, all other limits are for TA = Tj = 25'C (Note 6).
Parameter

CondItIons

Typleal

LImIt
(Note 2)

UnIts

5.00

4.85/4.75
5.15/5.25

Vmin
V max

Vbuffer (Pin 10)
Output Voltage

5 mA :S: 10 :S: 100 mA
6V:S: VIN:S: 26V
9V:S: VIN:S: 16V

2

25/25

mVmax

7V:S: VIN:S: 26V

5

50/50

mVrnax

Load Regulation

5 mA :S: Ibut:S: 100 mA

15

50/50

mVmax

Output Impedance

50 mAde and 10 mArms,
fo = 120 Hz

200

Quiescent Current

Ibuf

Output Noise Voltage

10 Hz-100 kHz, lOUT = 100 mA

Line Regulation

= 100mA

8.0

Long Term Stability
Ripple Rejection

fo=120Hz

Dropout Voltage

Ibut = 100 mA

Current Limit
Maximum Operational
Input Voltage

Continuous DC

Maximum Line
Transient

Vbuf"; 6V, Rbuf = 1000,
T,,; 100ms

Reverse Polarity
Input Voltage DC

Vbut;;' -0.6V, Rbut

Reverse Polarity Input
Voltage Transient

T:S: 100 ms, Rbut

= 1000

= 1000

mO

15/18

mAmax

100

f.£V

20

mVll000hr

70

60/S0

dBmin

0.35

0.50/0.80

V max

0.23

0.15/0.15

Amin

32

26/28

Vmln

65

60/80

Vmln

-30

-15/-15

Vmin

-55

-35/-38

Vmln

Electrical Characteristics
VIN = 14V, Istby = 1 mAo Cstby = 10 f.£F, unless otherwise indicated. Boldt. . type refers to limits over the entire operating
temperature range, -40'C :S: TA :S: + 125'C. all other limits are for TA = Tj = 25'C (Note 6).
Parameter

Typ1c81

CondItIons

Um"
(Note 2)

Units

V standby (Pin 9)
Output Voltage

1 mA :S: 10 :S: 7.5 mA
6V:s: VIN"; 26V

Line Regulation

9V:s: VIN:S: 16V

5.00

4.85/4.78
5.15/8.28

Vmln
V max

2

25/28

mVrnax

7V:s: VIN:S: 26V

5

50/80

mVmax

Load Regulation

0.5 mA :S: lOUT :S: 7.5 mA

6

50/110

mVmax

Output Impedance

5 mAde and 1 mA rms, fo = 120 Hz

Quiescent Current

Istby = 7.5 mA
Istby

= 2mA

2·71

0.9

0

1.2

2.0/4.0

mAmax

0.9

1.5/4.0

mAmax

•

Electrical Characteristics (Continued)
VIN = 14V, Istby = 1 mA, Cstby = 10 ,...F, unless otherwise indicated. Boldface type refers to limits over the entire operating
temperature range, - 40'C ,;; T A ,;; + 125'C, all other limits are for T A = Tj = 25'C (Note 6).
Parameter

Limit
(Note 2)

Conditions

Typical

Units

10 Hz-100 kHz,lstby = 1 mA

100

,...V

20

mV/1000 hr

Vstandby (Pin 9) (Continued)
Output Noise Voltage
Long Term Stability
Ripple Rejectiol'1

fo = 120 Hz

70

60/50

Dropout Voltage

Istby = 1 mA

0.26

0.50/0.60

Vmax

Istby = 7.5 mA

0.38

0.60/0.70

V max

Current Limit

dBmin

15

12/12

mAmin

Maximum Operational
Input Voltage

4;5V,;; Vstby ,;; 6V,
Rstby = 1000.0

65

60/60

Vmin

Maximum Line
Transient

Vstby';; 6V, T ,;; 100 ms,
Rstby = 1000.0

65

60/60

Vmin

Reverse Polarity
Input Voltage DC

Vstby:?: -0.6V,
.Rstby = 1000.0

-30

-15/-15

Vmin

Reverse Polarity Input
Voltage Transient·

T ,;; 100 ms, Rstby = 1000.0

-55

-35/-35

Vmin

Electrical Characteristics,
VIN = 14V, COUT = 10 ,...F, Cbuf = 10 ,...F, Cstby = 10 ,...F, unless otherwise indicated. Boldface type refers to limits over the
entire operating temperature range, -40'C ,;; TA ,;; + 125'C, all other limits are for T A = Tj = 25'C (Note 6).
Typical

Limit
(Note 2)

Units

lOUT';; 500 mA, Ibuf = 5 mA,
Istby';; 7.5 mA

±30

±100/± 100

mVmax

lOUT = 5 mA, Ibuf ,;; 100 mA,
Istby';; 7.5 mA

±30

±100/± 100

mVmax

VOUT-Vbuf

lOUT';; 500 mA, Ibuf ,;; 100 mA,
Istby = 1 mA

±30

±100/± 100

mVmax

Isolation'

ROUT = 1n,Ibuf ,;;100 mA

5.00

4.50/4.50
5.50/5.50

Vmin
Vmax

5.00

4.50/4.50
5.50/5.50

Vmin
V max

5.00

4.50/4.50
5.50/5.50

Vmin
V max

5.00

4.50/4.50
5.50/5.50

Vmin
Vmax

Parameter

Conditions

Tracking and Isolation
Tracking
VOUT-Vstby
Tracking
Vbuf-Vstby
Tracking

Vbuf from VOUT
Isolation'

ROUT = 10, Istby ,;; 7.5 mA

Vstby from VOUT
Isolation',

Rbuf = 1.0, lOUT ,;;500 mA

Vout from Vbuf
Isolation'

Rbuf = 1n, Istby ,;; 7.5 mA

Vstby from Vbuf

'isoiation refers to'the ability of the specified output to remain within the tested limits when the other output is shorted to ground.

2-72

Electrical Characteristics (Continued)
VIN = 14V, lOUT = 5 mA, Ibuf = 5 mA, Isjby = 5 mA, Rt = 130 kO, Ct = 0.33!-,F, Cmon = 0.47 !-,F, unless otherwise indicated,
Boldface type refers to limits over the entire operating temperature range, -40'C s: TA s: + 125'C, all other limits are for TA =
TJ = 25'C (Note 6)
Parameter

Conditions

Typical

Limit
(Note 2)

Units

Computer Monitor/Reset Functions

= 4V, Vrst = O.4V
= 4V, Irst = 1 mA

Ireset Low

VIN

Vreset Low

VIN

Rtvoltage

(Pin 2)

5

2/0.50

mAmin

0.10

0.40/0.40

Vmax

1.22

1.15/0.75

Vmin

1.22

1.30/2.00

Vmax

50

45/17.0

mSmln

50

55/80.0

mSmax

Power On Reset
Delay

V!-'P mon = 5V
(Tdly = 1.2 Rt Ct>

AVOUT Low
Reset Threshold

(Note 4)

AVOUTHigh
Reset Threshold

(Note 4)

Reset Output
Leakage

V!-'Pmon

= 5V, Vrst = 12V

!-'Pmon Input
Current (Pin 4)

V!-'Pmon

= 2.4V
= 0.4V

1.22

0.80/0.80

Vmln

1.22

2.00/2.00

Vmax

V!-'Pmon

-350

mVmin

-500/-550

mVmax

225/175

mVmin

750/800

mVmax

0.01

1/5.0

!-,Amax

7.5

25/25

!-,Amax

0.01

10/15

!-,Amax

600

P.Pmon Input
Threshold Voltage

-225/-175

p.P Monitor Resel
Oscillator Period

V!-'P mon = OV
(Twindow = 0.82 RtCmon)

50

45/30

mSmin

50

55/70

mSmax

p.P Monitor Reset
Oscillator Pulse Width

VP.Pmon = OV
(RESETpw = 2000 Cmon)

1.0

0.710.4

mSmln

1.0

1.3/2.10

mSmax

Minimum p.P Monitor
Input Pulse Width

(NoteS)

Reset Fall Time

= 10k, Vrst = 5V, Crst s: 10 pF
Rrst = 10k, Vrst = 5V, Crst s: 10 pF
VON = 2.4V
VON = 0.4V

Reset Rise Time
On/Off Switch Input
Current (Pin 8)

2

Rrst

On/Off Switch Input
Threshold Voltage

p.s

0.20

1.00/1.00

p.smax

0.60

1.00/1.50

p.smax

7.5

25/25

p.Amax

0.01

10/10

p.Amax

1.22

0.80/0.80

Vmin

1.22

2.00/2.00

Vmax

Nole 1: Thermal resistance without a heatslnk for Junctlon-to·case temperature Is 3'C/W. Thermal resistance case·to·amblent Is 40'C/W.
Nate 2: Tested Limits are guaranteed and 100% production tested.
Nate 3: Human body model, 100 pF capacitor discharged through a 15000 resistor.
Nate 4: Internal comparators detect when the main regulator output (Vour) changes from the measured output voltage (with VIN = 14V) by the specified amount,
.l.Vour High or .l.Vour Low, and set the Reset Error Flag low. The Reset Error Flag Is held low until Your returns to regulation. The Reset Error Flag Is then
allowed to go high again after a delay set by RI and Ct. (see application section).
Note 6: This parameter Is a measure of how short a pulse can be detected at the "p Monitor Input. This parameter Is primarily Influenced by the value of Cman.
(See Application Hints Section.)
Nole 6: To ensure constant Junction temperature, low duty cycle pulse testing I. used.

2-73

•

Block Diagram
ON/OFF SWITCH

11

1

VIN

8

ON/OFF
THERMAL SHUTDOWN

r~

I

POWER-UP
RESET
TIMER

I

9

Cti-

-

::!::,

VSTANDBY

-

L

SV. 100mA
REGULATOR

VOUT

.:I:.CstBY

VIN

3

I'P MONITOR

I

SV. 7.5 mA
REGULATOR

::!::,

.:I:.CoUT

VIN

VOUT
COMPARATOR ...
'l='S.SV
4.0V

2

i"-

SV.SOOmA
REGULATOR

10
JL ::::!::,

VSUFFER

CaUF
.:c.
-

-

PEAK DETECTOR
4

COMPUTER RESET
TIMER/OSCILLATOR
5

CwON

.:c.

~

7i~ST

1--

-

RESET

TLlH/II252-2

Pin Description
Pin No.

Comments

Pin Name

1

VIN
Rt
Ct
J.l.Pmon
Cmon
Ground
Reset

2
3
4
5

6
7

ON/OFF

8
9

Vstandby
Vbuffer
VOUT

10
11

Positive supply input voltage
Sets internal timing currents
Sets power·up reset delay timing
Microcomputer monitor input
Sets J.l.C monitor timing
Regulator ground
Reset error flag output
Enables/disables high current regulators
Standby regulator output (7.5 rnA)
Buffer regulator output (100 rnA)
Main regulator output (500 rnA)

External Components
Component

Typical Value

Component Range

Gt
Gtc
Rtc

1 p.F
130k
0.33p.F
0.01 p.F
10k

0.47 p.F-10 p.F
24k-1.2M
0.033 p.F-3.3 p.F
0.001 p.F-0.1 p.F
1k-100k

Cmon

0.47 p.F

0.047 p.F-4.7 p.F

Rrst

10k

5k-100k

Cstby

10 p.F

10 p.F-no bound

Cbul

10 p.F

10 p.F-no bound

COUT

10 p.F

10 p.F-no bound

CIN
Rt

Comments
Required if device is located far from power supply filter.
Sets internal timing currents.
Sets power-up reset delay.
Establishes time constant of AC coupled computer monitor.
Establishes time constant of AC coupled computer monitor. (See
applications section.)
Sets time window for computer monitor. Also determines period and pulse
width of computer malfunction reset. (See applications section.)
Load for open collector reset output. Determined by computer reset input
requirements.
A 10 p.F is required for stability but larger values can be used to maintain
regulation during transient conditions.
A 10 p.F is required for stability but larger values can be used to maintain
regulation during transient conditions.
A 10 p.F is required for stability but larger values can be used to maintain
regulation during transient conditions.

2·74

r-

i:

Typical Circuit Waveforms

N
CD

c»

35V

""

31V
INPUT
VOLTAGE
PIN I
ON/OFF
SWITCH
PIN 8
OUTPUT
VOLTAGE
PIN II
STANDBY
OUTPUT
PIN 9
Tlt.tING
CAPACITOR
PIN 3

4.6V

14V
OV
SV

OV

6V

SV

OV
5V
OV
2V

OV
RESET
VOLTAGE
PIN 7
J'P MONITOR
VOLTAGE
PIN 4

SV

OV
SV

IIII

OV
TURN
ON

HIGH
VIN

II
HIGH
VOUT

III
III
LOW
VOUT

/

COt.tPUTER
MALFUNCTION

II
TURN
OFF

J'P
MALFUNCTION

TUH/11252-3

Connection Diagram

/

TO-220 II-LEAD
TAB IS GROUND

11

0

"

MAIN OUTPUT

10

BUFFER OUTPUT

9

STANDBY OUTPUT

8

ON/OFF SWITCH

7

RESET ERROR FLAG

6

GROUND

5

J'P MONITOR CAPACITOR

4

J'P MONITOR INPUT

3

TIt.tING CAPACITOR

2

TIt.tING RESISTOR

•

INPUT VOLTAGE
TUH/11252-4

Order Number LM2984T
See NS Package Number TA11B

2-75

Typical Performance Characteristics
Dropout Voltage (VOUT)

Dropout Voltage (Vbur)

1.2
1.0

~

~
!i!
5

~

!

0.6

0.5

.e

0.8

loUT = 500 mA ".,. I--"

O.B

0.4 r 0.2

=:tt:L -

III
~

0..\ r -

..

0.2

!i!
5
~

Ii!

0
-50 -25 o 25 50 75 100 125 150

i

~

/
./

0.2

0.3

0.4

0.5

!

0.2

0.6

~

~

I
20

SOD Peak

:!

VIN " 14V

I

5

I

OA

Ia

==

20~

~

0
-50 -25 0

I.-

I

Io~T·l50 1A

r- r-

25 50 75 100 125 150

JUNCTION TEMPERATURE (DC)

ii:l

i

~

0.2 i"'"'

2

VIN =14V

100

30

I

2Or-

I

4 r-

-

r- lalu/ ",50 jA

Quiescent Current (Vatby)

ii3

0
-SO -25 0

r- r-

25 50 75 100 125 150

JUNCTION TEMPERATURE (oC)

25 SO 75 100 125 150

JUNCTION TEMPERATURE (Oc)

:!

I

f- VIN=14V

10

4.0

~u/"IOOmA

8

-

0
-50 -25 0

VIN ·14V

12

10

40

~

25 SO 75 100 125 150

loUT .ISTBY • 0

8

6

50 Peak Output Current (Vetby)

i:l

200 i"'"'

4

OUTPUT CURRENT (rnA)

Quiescent Current (Vbuf)

:!

...

i"'"'

0

:!

II

~U/ .ISTBy - 0

40~

OA

JUNCTION TEMPERATURE (Oc)

YIN "14V

.... louT • 500 mA

0.6

120

500

Quiescent Current (VOUT)

ii:l

100

Output Current (Vbur)

-SO -25 0

80

IO

60

400

JUNCTION TEMPERATURE (Oc)

:!

60

40

0

25 50 75 100 125 ISO

25 50 75 100 125 150

0.8

OUTPUT CURRENT (mA)

I

0
-50 -25 0

0.1

0
0

Peak Output Current (VOUT)

§

louT' 2mA

Dropout Voltage (Vslby)

~

OUTPUT CURRENT (A)

1.6

I-

I-

1.0

0
0.1

0.2

- JUNCTION TEMPERATURE (Oc)

0.6
0.-1

0
0

0.3

.....

! 1.1.
..... ~

_~UT·7.5mA

0
-50 -25 0

25 50 75 100 125 150

0.6

~
5
~

0.2

0.8

I

0.-1 r -

Dropout Voltage (Vbur)

~

,

0.-1

I

~
!i!

1.0

0.6

1.2

~
III

JUNCTION TEMPERATURE (oC)

0.8

3

....

0.1

Dropout Voltage (VOUT)

!i!
5

-

0,5

lciUT"50MA

I-'"

0
-50 -25 0

1.0

III
~

J
-I~~
.I I

o..l

JUNCTION TEMPERATURE (OC)

~

Dropout Voltage (Vslby)

0.6

i

I:1.0 r -

-

VIN -14V
I-VOUT o/r- r- rr-Ivau/ o/r - r - r -

l

I

2.0

l - e1.0

I~BYJ5LA- t7 ')

o I-e-I-Irrmt-I--50 -25 0

25 50 75 100 125 150

JUNCTION TEMPERATURE (DC)
TL/H111252-5

2-76

Typical Performance Characteristics
Quiescent Current (VOUT)

Quiescent Current (Vbud

100

<-

.5

i
~

~
~

<-

80

.5

3.0

16

60

./

40

L

12

~

./

l:i

,/

20

i

300

400

500

20

60

!Z

40

B

30

~

~~

I I I

~JT.~O+-

II"'--

10

-10
-10 -5

5

10

80

100

.5

15 20 25 30

120

o

10

OUTPUT CURRENT (mA)

Quiescent Current (Vstby)

IS

~

~
"u
is

10
IBur

"\"

)

l:i

-5
-10

ISTBY = 10mA-

=100 rnA

I

~

=50 rnA

IBUF

5

INPUT VOLTAGE (V)

10

15 20 25

30

Output Voltage (VOUT)

1sr~=imA I

-1
-10

10

INPUT VOLTAGE (V)

20

30

INPUT VOLTAGE (V)

Output Voltage (Vbud

7

_f--

4

~

I I I
I I I

J

60

.... - ..... f-

0.5

Quiescent Current (Vbuf)

<-

""\ ~J::IT-

20

40

20

I I I

50

1.5
1.0

OUTPUT CURRENT (mA)

Quiescent Current (VOUT)
70

2.0

o

o

600

iis
~

o
200

2.5

l:i

...... . /

~

./

<-

.5

~

OUTPUT CURRENT (mA)

<-

Quiescent Current (Vstby)

20

o -~
o 100

.5

(Continued)

7

Output Voltage (Vstby)

7

Reu, =10011

RouT' 10011

I'

-1
-40

RsTBY. I kll

I'
-20

20

40

I'

-20

INPUT VOLTAGE (v)

Low Voltage Behavior (VOUT)

lour = 250 rnA

20

-1
-40

-20

INPUT VOLTAGE (V)

6

Low Voltage Behavior (Vbud

/i

20

I-IBU

=500 rnA

o
o

o
INPUT VOLTAGE (V)

'= /

SOmA

6

Low Voltage Behavior (Vstby)

/

/
leUF

o

4

40

INPUT VOLTAGE (V)

/

/V /

loUT

40

ISTBY

=100 rnA

5

INPUT VOLTAGE (V)

I

=

1mA/ ISYBY = 7.5 rnA

o
o

3

4

5

INPUT VOLTAGE (V)

TUH/11252-6

2-77

•

00:1'

CD

~

~

Typical Performance Characteristics
Line Transient
Response (VOUT)
5
0

5

5

0

0
5
0

1\

II

1/

2

3
2

1
0
1
-10

0
1
-10

3

0
1
-10

10

20

30

40

50

80

1

0

Load Transient
Response (VOUT)

~;

100
100
0

0
5
0

LJ

.. 20

750
~_ 500

G~ 250
0
-250
-100

50

80

0

10

0-

150
100

BE

50
0
-50
-100 0

100 200 300 400 500 600

30

40

SO

60

Load Transient
Response (VSlby)
0
5

I"

\

I

0
5
0

.,I

5
0
100 200 300 400 500 600

-100 0

100 200 300 400 500 800
TIME (po)

TIME (1'0)

TIME (1'1)

Output Impedance (VOUT)

20

TIME (1'.)

\

I
V_

m'C'

~-

0

40

n

5

1\

I

30

20

5
0

0-

~-

20

Load Transient
Response (Vbut>

300

S~-10

o

11

TIME (1'.)

TIME (1'1)

... ~

5
0
5
0

r'\.

5
0

3
2
1

~z

Line Transient
Response (Vstby)

Line Transient
Response (Vbuf)

1\

5
0
5
0

~!

(Continued)

Output Impedance (Vbut>

Output Impedance (Vstby)

10

100

§

I
I:!
~

5

§

0.1

0.01
10
FREQUENCY (Hz)

.Ripple Rejection (VOUT)
90

lK

10

10K

11111

JT~~~~~'

lK

10K

Ripple Rejection (Vstby)
90 r-

111111111
111111

80

100

FREQUENCY (Hz)

Ripple Rejection (Vbut>
90

111111111

80

100

FREQUENCY (Hz)

10:

~lFLW61~A

~

70

70

80 ./

60

!iii

50

50

Ii!

40

40

~

I-80 I-I70
60

111111111
111111

'-1!TJrLIII~~-

P-

I-I-I--

50 l -

I-10

100

lK

FREQUENCY (Hz)

10K

10

100

lK

FREQUENCY (Hz)

10K

40 I...
10

100

lK

10K

FREQUENCY (Hz)

TL/H111252-7

2-78

Typical Performance Characteristics

(Continued)
Device Dissipation vs
Ambient Temperature

Output Voltage

~
w

~

5.30

22
20

5.20

IB

:g

5.10

z

5.00

~
iiii5

0

r-

~

~

i

4.90

0

4.BO
4.70
-50 -25

0

25

50

16

14
12
10
B

INFINITE HEAT SINK

...... 5°C/ W HEAT SINK

t-...
10OC/~

JUNCTION TEMPERATURE (OC)

r-..

.......

..... ""
NO HEAT SINK

HEIAT fiNK

o I
o 10

75 100 125 ISO

I
L

I'

20 30 40 50 60 70 BO 90 100
AMBIENT TEMPERATURE (oC)

TL/H/I1252-B

S

Output Capacitor ESR
(Standby Output, Pin 9)

_

100

Output Capacitor ESR
(Buffer Output, Pin 10)
CoUT

S
'V

"..
z

'1'

~

CoUT = 10)'F

..

~~~~~;- ~

I

!:l
~

~

8

0.0 I

1.5

3.0

4.5

= 10 pF

~0

10

7.5

STABLE
REGION -

I

OUTPUT CURRENT (mA)

!

100

= 10)'F

-

~-% ~
,~

10

STABLE
REGION _

~,

~
:;;
~

CoUT
~

la

--i

o. I ~/,

o.

~

I""'"

8 0.0 I

0.0 I

o

S

Output Capacitor ESR
(Main Output, Pin 11)

t!

i;l

:;;

I

o

100

TL/H/11252-9

20

40

60

BO

100

OUTPUT CURRENT (mA)

TL/H/11252-10

TUH/11252-ll

o

100

200

300

400

500

OUTPUT CURRENT (mA)
TLlH/11252-12

Application Hints
outputs are controlled with the ON/OFF pin described later,
the standby output remains on under all conditions as long
as sufficient input voltage is supplied to the IC. Thus, memory and other circuits powered by this output remain unaffected by positive line transients, thermal shutdown, etc.
The standby regulator circuit is designed so that the quiescent current to the IC is very low « 1.5 mAl when the other
regulator outputs are ciff.
The capacitor on the output of this regulator can be increased without bound. This will help maintain the output
voltage during negative input transients and will also help to
reduce the noise on all three outputs. Because the other
two track the standby output: therefore any noise reduction
here will also reduce the other two noise voltages.

OUTPUT CAPACITORS
The LM2984 output capacitors are required for stability.
Without them, the regulator outputs will oscillate, sometimes
by many volts. Though the 10 ",F shown are the minimum
recommended values, actual size and type may vary depending upon the application load and temperature range.
Capacitor effective series resistance (ESR) also affects the
Ie stability. Since ESR varies from one brand to the next,
some bench work may be required to determine the minimum capacitor value to use in production. Worst case is
usually determined at the minimum ambient temperature
and the maximum load expected.
Output capacitors can be increased in size to any desired
value above the minimum. One possible purpose of this
would be to maintain the output voltages during brief conditions of negative input transients that might be characteristic of a particular system.
Capacitors must also be rated at all ambient temperatures
expected in the system. Many aluminum type electrolytics
will freeze at temperatures less than -30'C, reducing their
effective capacitance to zero. To maintain regulator stability
down to -40'C, capacitors rated at that temperature (such
as tantalums) must be used.
Each output must be terminated by a capacitor, even if it is
not used.

BUFFER OUTPUT
The buffer output is deSigned to drive peripheral sensor circuitry in a ",p system. It will track the standby and main
regulator within a few millivolts in normal operation. Therefore, a peripheral sensor can be powered off this supply and
have the same operating voltage as the ",p system. This is
important if a ratiometric sensor system is being used.
The buffer output can be short circuited while the other two
outputs are in normal operation. This protects the ",p system from disruption of power when a sensor wire, etc. is
temporarily shorted to ground, i.e. only the sensor signal
would be interrupted, while the ",p and memory circuits
would remain operational.

STANDBY OUTPUT
The standby output is intended for use in systems requiring
standby memory circuits. While the high current regulator

The buffer output is similar to the main output in that it is
controlled by the ON/OFF switch in order to save power in
2-79

•

Application Hints (Continued)
the standby mode. It is also fault protected against overvoltage and thermal overload. If the input voltage rises above
approximately 30V (e.g. load dump), this output will automatically shut down. This protects the internal circuitry and
enables the IC to survive higher voltage transients than
would otherwise be expected. Thermal shutdown is necessary since this output is one of the dominant sources of
power dissipation in the IC.

DELAYED RESET
Resistor Rt and capacitor Ct set the period of time that the
RESET output is held low after a main output error condition
has been sensed. The delay is given by the formula:
T dly = 1.2 RtCt (seconds)
The delayed RESET will be initiated any time the main output is out of regulation, i.e. during power-up, short circuit,
overvoltage, low line, thermal shutdown or power-down.
The JlP is therefore RESET whenever the output voltage is
out of regulation. (It is important to note that a RESET is
only initiated when the main output is in error. The buffer
and standby outputs are not directly monitored for error
conditions.)

MAIN OUTPUT
The main output is designed to power relatively large loads,
i.e. approximately 500 mA. It is therefore also protected
against overvoltage and thermal overload.
This output will track the other two within a few millivolts in
normal operation. It can therefore be used as a reference
voltage for any signal derived from Circuitry powered off the
standby or buffer outputs. This is important in a ratiometric
sensor system or any system requiring accurate matching of
power supply voltages.

JlP MONITOR RESET
There are two distinct and independent error monitoring
systems in the LM2984. The one described above monitors
the main regulator output and initiates a delayed RESET
whenever this output is in error. The other error monitoring
system is the JlP watchdog. These two systems are OR'd
together internally and both force the RESET output low
when either type of error occurs.
This watchdog circuitry continuously monitors a pin on the
JlP that generates a positive going pulse during normal operation. The period of this pulse is typically on the order of
milliseconds and the pulse width is typically on the order of
10's of microseconds. If this pulse ever disappears, the
watchdog circuitry will time out and a RESET low will be
sent to the JlP. The time out period is determined by two
external components, Rt and Crnon, according to the formula:
Twindow = 0.82 RtCrnon (seconds)
The width of the RESET pulse is set by Crnon and an internal resistor according to the following:
RESETpw = 2000 Crnon (seconds)
A square wave signal can also be monitored for errors by
filtering the Crnon input such that only the positive edges of
the Signal are detected. Figure 2 is a schematic diagram of a
typical circuit used to differentiate the input signal. Resistor
Rtc and capacitor Ctc pass only the rising edge of the
square wave and create a short positive pulse suitable for
the JlP monitor input. If the incoming Signal continues in a
high state or in a low state for too long a period of time, a
RESET low will be generated.

ON/OFF SWITCH
The ON/OFF switch controls the main output and the buffer
output. The threshold voltage is compatible with most logic
families and has about 20 mV of hysteresis to insure 'clean'
switching from the standby mode to the active mode and
vice versa. This pin can be tied to the input voltage through
a 10 kn resistor if the regulator is to be powered continuously.
POWER DOWN OVERRIDE
Another possible approach is to use a diode in series with
the ON/OFF Signal and another in series with the main output in order to maintain power for some period of time after
the ON/OFF signal has been removed (see Figure 1). When
the ON/OFF switch is initially pulled high through diode D1,
the main output will turn on and supply power through diode
D2 to the ON/OFF switch effectively latching the main output. An open collector transistor Q1 is connected to the
ON/OFF pin along with the two diodes and forces the regulators off after a period of time determined by the JlP. In this
way, the JlP can override a power down command and store
data, do housekeeping, etc. before reverting back to the
standby mode.

JTT
O-N-/O-FF-~R1~~D;-:~~,8!:F-l:""';~::;-2""":;~R72::.:.11
MAINI11

MAIN OUTPUT

OUTPUT I

ON/OFF

...

CONTROL

10 pF

10kll~~

S~~~O~:

'i

,

10k1l

rI7

..LL
..............

..oJ
TL/H/11252-13

L.J

L..

ctc

!

~l----p--J
Ric

FIGURE 1. Power Down Override

lil

RESET OUTPUT
This output is an open collector N PN transistor which is
forced low whenever an error condition is present at the
main output or when a JlP error is sensed (see JlP Monitor
section). If the main output voltage drops by 350 mV or rises
out of regulation by 600 mV typically, the RESET output is
forced low and held low for a period of time set by two
external components, Rt and Ct. There is a slight amount of
hysteresis in these two threshold voltages so that the RESET output has a fast rise and fall time compatible with the
requirements of most JlP RESET inputs.

pP MONITOR INPUT

jcmon
TL/H/11252-14

FIGURE 2. Monitoring Square Wave JlP Signals
The threshold voltage and input characteristics of this pin
are compatible with nearly all logic families.
There is a limit on the width of a pulse that can be reliably
detected by the watchdog circuit. This is due to the output
resistance of the transistor which discharges Crnon when a
high state is detected at the input. The minimum detectable
pulse width can be determined by the following formula:
PWrnin = 20 Crnon (seconds)

2-80

m

.0
C

Dl
CD

..en
::::s

n

~

CD

..
3
II)

(;'

c

w"

cc
D1
3

~

t86~W'

~National

~ semiconductor
LM2990
Negative Low Dropout Regulator
General Description

Features

The LM2990 is a three-terminal, low dropout, 1 ampere negative voltage regulator available with fixed output voltages
of -5, -5.2, -12, and -15V.
The LM2990 uses new circuit design techniques to provide
low dropout and low quiescent current. The dropout voltage
at 1A load current is typically O.6V and a guaranteed worstcase maximum of 1V over the entire operating temperature
range. The quiescent current is typically 1 mA with 1A load
current and an input-output voltage differential greater than
3V. A unique circuit design of the internal bias supply limits
the quiescent current to only 9 mA (typical) when the regulator is in the dropout mode (VOUT - VIN :s: 3V). Output voltage accuracy is guaranteed to ± 5% over load, and temperature extremes.
The LM2990 is short-circuit proof, and thermal shutdown
includes hysteresis to enhance the reliability of the device
when overloaded for an extended period of time. The
LM2990 is available in a 3-lead TO-220 package and is rated for operation over the automotive temperature range of
-40'C to +125'C.

•
•
•
•
•
•
•

5% output accuracy over entire operating range
Output current in excess of 1A
Dropout voltage typically O.6V at 1A load
Low quiescent current
Internal short circuit current limit
Internal thermal shutdown with hysteresis
Functional complement to the LM2940 senes

Applications
• Post switcher regulator
• Local, on-card, regulation
• Battery operated equipment

Output Voltages
LM2990T-5.0

-5V

LM2990T-5.2
LM2990T-12

-5.2V
-12V

LM2990T-15

-15V

Typical Application

-b+~10}olF
T Go' _ _""'_",
IGND
Unregulated
Input

T

VIN

'Required if the regulator is located further than
6 inches from the power supply filter capacitors.
A 1 "F solid tantalum or a 10 "F alUminum
electrolytic capaCitor Is recommended.

ic:.
T

l0}olF

LM2990 1----4~Vo

Regulated
Output
TL/H/l0801-1

"Required for stability. Must be at least a 10 "F
aluminum electrolytic or a 1 "F solid tantalum
to maintain stability. May be increased without
bound to maintain regulation during transients.
Locate the capacitor as close as possible to the

regulator. The equivalent series resistance
(ESR) is critical, and should be less than 10n

over the same operating temperature range as
the regulator.

Connection Diagram and Ordering Information
3-Lead To-220

TLlH/l0801-2

Front View

Order Number LM2990T-5.0, LM2990T-5.2, LM2990T-12 or LM2990T-15
See NS Package Number T03B

2-82

Absolute Maximum Ratings

(Note 1)
-65·C to + 150"C

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Input Voltage
-26Vto +0.3V

Storage Temperature

ESD Susceptibility (Note 2)
Power Dissipation (Note 3)

Junction Temperature Range (TJ)
Maximum Input Voltage (Operational)

Operating Ratings

2kV
Internally Limited
125·C

Junction Temperature (TJmax)

260·C

Lead Temperature (Soldering, 10 sec.)
(Note 1)

- 40·C to + 125·C
-26V

Electrical Characteristics VIN = -5V + VO(NOM) (Note 6),10 = 1A, Co = 47 "F, unless otherwise specified.
Boldface limits apply over the entire operating temperature range, -40·C ,;;: TJ ,;;: 125·C, all other limits applyforTJ = 25·C.
LM2990T-S.O
Parameter
Output Voltage (Vo)

Conditions

Typ
(Note 4)

5mA,;;: 10"; 1A
-5

10=5mA,
VO(NOM) -1V

-4.90
-5.10

LM2990T-S.2
Typ
(Note 4)

-5.2

-4.75
-5.25

5mA,,; 10"; 1A
Line Regulation

Limit
(NoteS)

4

> VIN > -26V

40

4

Limit
(Note S)

Units
(Limit)

-4.94
-5.46

V (max)
V (min)
V
V (max)
Vlminl

40

mV(max)

-5.10
-5.30

Load Regulation

50 rnA ,,; 10"; 1A

1

40

1

40

mV(max)

Dropout Voltage

10 = 0.1A, aVO"; 100 mV

0.1

0.3

0.1

0.3

V (max)

10 = 1A, aVo"; 100 mV

0.6

1

0.6

1

V (max)

1

5

1

5

mA(max)
mA(max)

Quiescent Current (Iq)

10"; 1A

9

50

9

50

Short Circuit Current

RL = 10 (Note 7)

1.8

1.5

1.8

1.5

A (min)

Maximum Output Current

(Note 7)

1.8

1.5

1.8

1.5

A (min)

Ripple Rejection

V'ippls = 1 Vrms,
frippls = 1 kHz, 10 = 5 mA

58

50

58

50

dB (min)

Output Noise Voltage

10 Hz-100 kHz, 10 = 5 rnA

250

750

250

750

"V (max)

Long Term Stability

1000 Hours

2000

10 = 1A, VIN = VO(NOM)

2000

ppm

fII

2·83

Electrical Characteristics VIN = -5V + VO(NOM) (Note 6),10 = 1A, Co = 47 ~F, unless otherwise specified.
Boldtac.limits apply over the entire operating temperature range, -40"C ~ TJ ~ 125'C, all other limits apply for TJ = 25'C.
(Continued)
LM2990T·12
Parameter
Output Voltage (Vo)

Conditions
5 mA

~

10

~

1A

5mA

~

10

~

1A

Typ
(Note 4)

-12

Line Regulation

10 = 5mA,
VO(NOM) -tV> VIN

Load Regulation

50 mA

Dropout Voltage

10

Quiescent Current (Iq)

~

10

~

Limit
(Note 5)
-11.76
-12.24

LM2990T·15
Typ
(Note 4)

-15

-11.40
-12.80

>

6

-26V

1A

= 0.1A,/No ~ 100 mV
10 = 1A, aVO ~ 100 mV
10 ~ 1A

= 1A, VIN = VO(NOM)
= 10 (Note 7)

60

6

Limit
(Note 5)

Units
(Limit)

-14.25
-15.75

V (max)
V (min)
V
V (max)
V (min)

60

mV(max)

-.14.70
-15.30

3

50

3

50

mV(max)

0.1

0.3

0.1

0.3

V (max)

0.6

1

0.6

1

V (max)

1

5

1

5

mA(max)

9

50

9

50

mA(max)

1.2

0.9

1.0

0.75

A (min)

(Note 7)

1.8

1.4

1.8

1.4

A (min)

Vrlppl e = 1 Vrms,
frlPPl a = 1 kHz, 10

52

42

dB (min)

600

1800

/J-V(max)

10
Short Circuit Current

RL

Maximum Output Current
Ripple Rejection

52

42

Output Noise Voltage

= 5 mA
10 Hz-100 kHz, 10 = 5 mA

500

1500

Long Term Stability

1000 Hours

2000

2000

ppm

Note 1: Absolute Maxlmum Ratings Indicate limits beyond which damage to the device may occur. Operating Ratings Indicate condlUons for which the device Is
Intended to be functional, but do not guarantee speclflo performance limits. For guaranteed specifications and teat conditions, see the Electrical Characteristics.
Note 2: Human body model, 100 pF dlschargsd through a 1.5 kG resistor.
Note 3: The maxlmum power dissipation Is a function of TJmlX' 6JA. and TA. The maximum allowable power dissipation at any ambient temperature Is Po ~ (TJmlX
- TIJ16JA. If this dl~slpatlon Is exceeded, the die temperature will rise above 125'C, and the LM2990 will eventually go Into thermal shutdown at·a TJ of
approximately 160'C. For the LM2990, the lunctlon-tOoamblent thermal resistance, Is 53'C/W, and the lunctlon·to-case thermal resistance Is 3'CIW.
Note 4: Typlcals are at TJ - 25'C and represent the most likely parametrlo norm.
Note 6: Umlt. are guaranteed and 100% production tested.
Note 8: VO(NOM) Is the nominal (typloal) regulator output voltage, -5V, -5.2V, -12V or -15V.
Note 7: The short circuit current Is less than the maximum output current with the -12V and -15V versions due 10 Internal foldback current limiting. The -5V and
- 5.2V versions, tested with a lower Input voltage, does not reach the foldback current limit and therefore conducts a higher short circuit current level. If the
LM2990 output Is pulled above ground, the maximum allowed current sunk back Into the LM2990 Is 1.5A.

Definition of Terms
Dropout Voltage: The Input-output voltage differential at
which the circuit ceases to regulate against further reductlon In Input voltage. Measured when the output voltage has
dropped 100 mV from the nominal value obtained at (Vo +
5V) input, dropout voltage is dependent upon load current
and junction temperature.
Input Voltage: The DC voltage applied to the input terminals with respect to ground.
Input·Output Differential: The voltage difference between
the unregulated input voltage and the regulated output voltage for which the regulator will operate.
Line Regulation: The change in output voltage for a
change in the input voltage. The measurement is made under conditions of low dissipation or by using pulse techniques such that the average chip temperature is not significantly affected.

Load Regulation: The change In output voltage for a
change in load current at constant chip temperature.
Long Term Stability: Output voltage stability under accellerated life-test conditions after 1000 hours with maximum
rated voltage and Junction temperature.
Output Noise Voltage: The rms AC voltage at the output,
with constant load and no input ripple, measured over a
specified frequency range.
Quiescent Current: That part of the positive input current
that does not contribute to the positive load current. The
regulator ground lead current.
Ripple ReJection: The ratio of the peak-to-peak input ripple
voltage to the peak-to-peak output ripple voltage.
Temperature Stability of VOl The percentage change in
output voltage for a thermal variation from room temperature to either temperature extreme.

2-84

.-

3:

Typical Performance Characteristics
Dropout Voltage
1.0

w

~g

TJ ;;; 125°C

0.6

~

TJ

"

=25°C ,lA ..-:::
~

0.4

~

Normalized Output Voltage
......

..... k:: ~ = -40°C
pI I

0.2

o~
o

I I I
I I I

....1IIIP
0.2

0.4

0.6

0.8

1.0

~

24

1.008

1

1.00 6

:g

1.004

a

~o

1.002

-

1.000,....,
0.998

8

i

~

~

0.994

itl

II

20

50

80

-10

lA

I
I

-~

o

-5

-10

-IS

-20

-25

110 125

II
II
10 =

100:;'A

•I..,

I
1"'\
o

o

-5

-10

-15

-20

-25

-30

o

-5

INPUT VOLTAGE (v)

INPUT VOLTAGE (v)

LM2990-5 and LM2990-5.2
Low Voltage Behavior

~~

80

-IO~

o
-30

50

LM2990-15
Quiescent Current

'0= 100mA

1'1

20

JUNCTION TEMPERATURE, TJ (OC)

I-"""'" "I
I
I

'0"100

o

-

-40

110125

\

-"""""'1

NoIHEATJ~

10

10 =

I--amA

~

..............10 0 C!W HEAT SI~K\

LM2990-12
Quiescent Current

1110 = IA

g

12

o
-10

10

"<
.5

15

JUNCTION TEMPERATURE, TJ (oC)

LM2990-5.0 and LM2990-5.2
Quiescent Current

II

\

I I ,
I I 1\

0.992
0.990
-40

r-- INF:NITE HEAT SINK

18

~

0.996

OUTPUT CURRENT (A)

10

o

Maximum Power
Dissipation (TO-220)

1.01 0

I I I
I I I

0.8

E

N
CD
CD

-10

-15

-20

-25

-30

INPUT VOLTAGE (V)

LM2990-5 and LM2990-5.2
Line Transient Response

LM2990-5 and LM2990-5.2
Load Transient Response

-6
-5

Io!

,---

IA

/

Co = 47"F

i

lo=10omAII

83

I\.

I

o
o

-I

-2

~S"

.. E

-4

-5

-6

-7

20

E

~

0

>

~

~M299~T-15

I

10 = IA

/f

-12

/

-9

40

0

-3

o

o

J

U,12990T-l

-6

-9

-12

20

r-

Co = 47 "F
'0

=

-IS

-18

40

60

80

100

TIME (".) .

LM2990-12 and LM2990-15
Load Transient Response

~

100mAIr

B3

Co

llf

TJ

= 47 pr

= 25°C

51
9

11\

V
INPUT VOLTAGE (v)

If

100

I\.

/

-3

80

f\

-50

LM2990-12 and LM2990-15
Line Transient Response

/

-6

60

50

TIME (".)

LM2990-12 and LM2990-15
Low Voltage Behavior
-IS

~~

§~

INPUT VOLTAGE (v)

-18

!:l~

0",
>0

~

-3

= 25°C

0

I\.

~

TJ

9

/

,Y
f

Co = 47 "r

lr

20

40

60

TIME (".)

80

100

!:l~
0",
>0

~~

50

~~
§~

-SO

II

1\

It
20

40

60

80

100

TIME (p.)
TL/HI10BOI-3

2-85

g

f.:I

:!

Typical Performance Characteristics
LM2990-S and LM299Q-S.2
Ripple Rejection
.0
.0

....~

70

~

.0

iii

40

i

30

F-

(Continued)

LM2990-S and LM2990-S.2
Output Impedance

Maximum Output Current
3

Co e 471'F
10 = SmA

a

.5

Ii

r"

50

-

~!!

r-.

~

'"

20

to

I

Ik

100

1000

100

1M

Ik

LM2990-12 and LM2990-15
Ripple Rejection

:!

70

50

iil

40

i

30

lOOk

o
o

1M

LM2990-12 and LM2990-1S
Output Impedance
1.8

3

.5
~

i13

~!!

i"o

i

~

20

0

to
0
Ik

100

lOOk

1M

tOO

Ik

fREGIIEHCY (Hz)

10k

-15

-20

-25

-3D

Maximum Output Current

a

r--

100

-10

2.0

471'F
'o.5mA

'"

-5

INPUT-OUTPUT DIFFERENTIAL (v)

Co •

'0

B

10k

FREQUENCY (Hz)

FREGIIEHCY (Hz)

'0
.0

................

0

0

tOO

--

lOOk

I

............ ~lOUT=

1.4

\'IN - YOUT

::I

-10Y

VIN - YOUT .. -15V

1.2

-~

VIN - Ywr .= "21V

1.0

I

0.8
-40

1M

-s'

1.6

-10

20

50

80

110 125

JUNCTION TEMPERATURE, TJ (OC)

FREQUENCY (Hz)

TUH/l0BOI-4

Application Hints
EXTERNAL CAPACITORS
The LM2990 regulator requires an output capacitor to maintain stability. The capacitor must be at least 10 /AoF aluminum
electrolytic or 1 /AoF solid tantalum. The output capacitor's
ESR must be less than 10n, or the zero added to the regulator frequency response by the ESR could reduce the
phase margin, creating oscillations (refer to the graph on
the right). An Input capacitor, of at least 1 /AoF solid tantalum
or 10 /AoF aluminum electrolytic, is also needed If 1he regulator Is situated more than 6" from 1he input power supply
filter.

Output CapaCitor ESR

:s...

20r--r--r--r--r-~

10

l£

~

'"f:3
~

8
....
::
§

FORCING THE OUTPUT POSITIVE
Due to an internal clamp circuit, the LM2990 can withstand
positille lIoltages on its output. If the lIoltage source pulling
the output positive is DC, the current must be limited to
I.SA. A current over I.SA fed back into the LM2990 could
damage the delilce. The LM2990 output can also withstand
fast positive lIoltage transients up to 26V, without any current limiting of the source. However, if the transients have a
duration of over 1 ms, the output should be clamped with a
Schottky diode to ground.

1.0

0.1

0.02

'--_L...._L...._L...._.L----I

0.0

0.25

0.5

0.75

1.0

1.25

OUTPUT CURRENT (A)
TL/H/l0801-9

2-86

,-----------------------------------------------------------------------------, r

:s:::

Typical Applications

N
fD
fD

o

Post Regulator for an Isolated Switching Power Supply
+12V INPUT

+5V
@400mA

+

I

10PF

+VIN

SW
COMP
150

LM2577ADJ

FB

Uk
+

I

+ 4.7

-

100

pF
TL/H/l0801-5

The LM2490 is a positive 1A low dropout regulator; refer to its datasheet for further information.

Fixed Current Sink
COMMON r - - -.....- - - - -....--I

R

VIN

Your

-24V ~-......~LM2990-5.0~;.;.-._t

TL/H/l0801-7

Adjustable Current Sink
COMMON r---"9-------<:~_iLg~J_

-24Vo--~~~

Co

10pF

f
TL/H110801-10

2-87

LM2990

m

.a
c::

~.

CD

::J

,

,

"

,

,

,

GIlD

,

"

U)

,I-'g.
'"CD~
n

Uk

I\l

8l

30p

300

20k

50

0.035

VIN

TUH/10801-8

~National

~ Semiconductor

LM2991 Negative Low Dropout Adjustable Regulator
General Description

Features

The LM2991 is a low dropout adjustable negative regulator
with a output voltage range between -2V to -25V. The
LM2991 provides up to 1A of load current and features a
On/Off pin for remote shutdown capability.
The LM2991 uses new circuit design techniques to provide
a low dropout voltage, low quiescent current and low temperature coefficient precision reference. The dropout voltage at 1A load current Is typically O.BV and a guaranteed
worst-case maximum of 1V over the entire operating temperature range. The quiescent current Is typically 1 mA with
a 1A load current and an Input-output voltage differential
greater than 3V. A unique circuit design of the Internal bias
supply limits the quiescent current to only 9 mA (typical)
when the regulator Is In the dropout mode (VOUT - Y,N
:s: 3V).
The LM2991 Is short-circuit proof, and thermal shutdown
Includes hysteresis to enhance the reliability of the device
when Inadvertently overloaded for extended periods. The
LM2991 Is available In a 5-lead TO-220 and Is rated for
operation over the automotive temperature range of -40'C
to + 125'C.

•
•
•
•
•
•
•
•

Output voltage adjustable from -2V to -25V
Output current in excess of 1A
Dropout voltage typically O.BV at 1A load
Low quiescent current
Internal short circuit current limit
Internal thermal shutdown with hysteresis
TIL, CMOS compatible ()I\J/OFF switch
Functional complement to the LM2941 series

Applications
• Post switcher regulator
• Local, on-card, regulation
• Battery operated equipment

Typical Application

+

Co"

IOl'r
unregUI~!:~

_ ...........:!.I
ON/orr

TL/H/II260-1
VOUT

• Required If the regulator Is located further than 6 Inches from the power
supply filter capaCitors. A 1 f'F solid tantalum or a 10 f'F aluminum electro·
lytiC capacitor Is recommended.
"Required for stability. Must be at least a 10 f'F aluminum electrolytic or a
1 f'F solid tantalum to maintain stability. May be Increased without bound to
maintain regulation during transients. Locate the capaCitor as close as possl·
ble to the regulator. The equivalent serie. re.'stance (ESR) Is critical. and
should be less than Ion over the same operating temperature range as the
regulator.

= VREF (1 + R2/Rl)

Connection Diagrams and Ordering Information
5-Lead TO-220
Straight Leads

~

fII

5-Lead TO-220
Bent, Staggered Leads

Eii

5-0utPut

4321-

54321-

Ground
Input
On/Off
Adjust

Output
Ground
Input
On/Off
Adjust
TL/H/11260-2

TL/H/I1260-9

Front View
Order Number LM2991T
See NS Package Number T05A

Front View
Order Number LM2991T
See NS Package Number T05D

2-89

Absolute Maximum Ratings

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and speclficaUons.
Input Voltage
- 26V to + 0.3V
ESD Susceptibility (Note 2)
2kV
Power Dissipation (Note 3)
Internally limited
Junction Temperature (TJrnaxl
125°C

Storage Temperature Range
Lead Temperature (Soldering, 10 sec.)

-65"C to

+ 150"C
230°C

Operating Ratings (Note 1)
Junction Temperature Range (TJ)
-40"C to
Maximum Input Voltage (Operational)

+ 125°C
-26V

Electrical Characteristics VIN = -10V, Vo = -3V,10 = 1A, Co = 47 }LF, R1 = 2.7k, TJ = 25°C, unless
otherwise speCified. Boldface limits apply over the entire operating junction temperature range.
Parameter
Reference Voltage

Conditions
5mA,,; 10"; 1A

Typical
(Note 4)

Min

Max

Units

-1.210

-1.234

-1.186

V

-1.27

-1.15

V

-3

V

0.004

0.04

%IV
%

5mA,,; 10"; 1A,
Vo - 1V ;;, VIN ;;, -26V
Output Voltage
Range

-2
-25

VIN = -26V

-24

V

Line Regulation

10 = 5mA, Vo -1V;;, VIN;;' -26V

Load Regulation

50 mA,,; 10"; 1A

0.04

0.4

Dropout Voltage

10 = 0.1A, AVo"; 100 mV

0.1

0.2

0.3
10 = 1A, AVo"; 100 mV

0.8

0.6

1
Quiescent Current

10"; 1A

Dropout Quiescent
Current

VIN = VO,IO ,,; 1A

Ripple Rejection

Vripple = 1 Vrms, fripple = 1 kHz,
10=5mA

60

Output Noise

V
V

0.7

5

mA

16

50

mA

50

dB

10 Hz - 100 kHz, 10 = 5 mA

200

450

ON/OFF Input
Voltage

(VOUT:ON)
(VOUT:OFF)

1.2
1.3

0.8

ON/OFF Input
Current

Voo/OFF = 0.8V (VOUT: ON)
VCR/OFF = 2.4V (VOUT: OFF)

0.1
40

10
100

}LA

Output Leakage
Current

VIN = -26V, VOO/OFF = 2.4V
VOUT = OV

60

250

)LA

Current Limit

VOUT = OV

2

2.4

1.5

}LV
V

A

Nole 1: Absolute Maximum Ratings indicate limits beyond which damage to the devioe may occur. Operating Ratings Indicate conditions for which the deivce is
intended to be functional. but do not guarantee specHlc perlormanoe limits. For guaranteed specifications and test condRions. see the Electrical Characteristics.
Nola 2: Human bcdy model. 100 pF discharged through a 1.5 kn resistor.
Nole 3: The maximum power dissipation is a function of TJrnax. 8JA and TA. The maximum allowable power dissipation at any ambient temperature is Po = (TJmax
- T/'J/8JA. 11 this dissipation is exceeded. the die temperature will rise above 125'C and the LM2991 will go into thermal shutdown. For the LM2991. the junctionto-ambient thermal resistenoe is 53'C/W. and the junction-to-case thermal resistenoe is 3'C/W.
Nole 4: Typicals are at TJ = 25'C and represent the most likely parametric norm.

2-90

r-

is:

Typical Performance Characteristics
Dropout Voltage
'.0

E

~
g

0.6

~

0.4

~

1
1
1

0.8

1 1
1 1

1/ ,

V"
po

~

:.;'1

o 1/
o

0.4

0.6

~

1.006
1.004

§

1.000

S

i

TJ = -55°C

-25

E

0.998

0.8

0.996
0.994

-40 -,0

OUTPUT CURRENT (A)

~

~
~

j"

~

50

80

-10

-15

-20

110

o

140

o

o

-25

Maximum Output Current

0 = jOOmA

r--

TJ = 25°C

'0= 100mA

VO=5V

.......

-'0

o

-15 -20 -25 -30

I

1.8

:3
B

!;

!;

i' 1~~.~.tOUTt -5J.

1.6

Y,N - Your = -;Xv

'.4
1.2

TIWE (1'5)

Ripple Rejection

z

~

iii
~

'"

JUNCTION

TI"E (1'0)

lk

%=47I'F
80 1o=5mA
VO=5V
70

~

50
40

O!!

30

~
~

20

50

80

110 '25

TJ (oC)

24
21

:g
z

100

~
2i
"

10

\

18
15
12

........ ~OC/w

0
10k

lOOk

FREQUENCY (Hz)

I~

I
'00

NO HEAl SINK ......... t-..,

o
Ik

10k

lOOk

FREQUENCY (Hz)

IN

\
HEAT SINK '"

l"--..

i

10
lk

20

TE~PERATURE.

INFINITE HEAT SINK

-a3

60

'00

I

Maximum Power
Dissipation (TO·220)

Output Impedance

90

1D
3

~

0.8
-40 -10

'00

-~

Y,N -Vour =-21V

'.0
80

-

VIN-Vour--15V

0

60

-30

Maximum Output Current

i
40

-10 -15 -20 -25

2.0

~

20

-5

INPUT-OUTPUT DIFFERENTIAL (v)

11\

'00

i"--....

~

%=47I'F
, I--,If..l-+++-+-+-TJ = 25°C
VO=5V

80

-25

3

Load Transient Response

%=47I'F

60

-20

INPUT VOLTAGE (V)

INPUT VOLTAGE (v)

Line Transient Response

40

-'5

-10

-5

TJ (OC)

o
-5

OUTPUT VOLTAGE (v)

20

Yo = -3V

- I--

1"\
-5

V

/

/

-5

(
o

TE~PERATURE.

7,'

g

o
o

-10

1\

'"

/

Vo= - 2 V

10= IA

1.0-'1"

500

~
~

Vo = -5V
TJ = 25°C

1o=5mA
,0N,00kHz

.3

-15

Quiescent Current

'0

TJ = 25°C

-;:

20

JUNCTION

Output Noise Voltage
'000

~g

0.990

'.0

10 =~.IA

-20

~

!-' -

1.002

~ 0.992

1 1
1 1

0.2

1.008

e

~
~

w

CQ
.....

Output Voltage

Normalized Output Voltage

TJ = 25°C

0.2

CQ

1.010

TJ = 150°C

t:;$i

N

\

r-.,.\

-40 -10

20

50

80

110

140

JUNCTION TE"PERATURE. TJ (OC)
TL/H111260-3

2-91

~ r-----------------------------------------------------~------------------------------,

m

re

:!i

Typical Performance Characteristics

ON/OFF Control Voltage

Adjust Pin Current

5r-~--'---r-~--,

!i

I

1o=IA

I

~

2.4 - -

--

----

2F~~~~__-r__+-~

o.~l--_...._-±~-_-_~~::_"'_'t'_.._--+"'___
!=I
O~~--~--~~--~

-50

-10

30

70

110

JUNCTION TEMPERATURE, TJ CGe)

150

Low Voltage Behavior
-18

80

J

~

(Continued)

~

I

70
10
50

Vo-=- 15V

-15

--

L1i
Vo

/

........

/

VJ.5V

I

/

40
30
-40 -10

20

SO

10

o
o

110 140

I

J

JUNCTION TEMPERATURE, TJ CGe)

-3

12V

-8

-I

-12 -15 -18

INPUT VOLTAOE (V)
TL/H/11260-4

Application Hints
Output Capacitor ESR

EXTERNAL CAPACITORS
The LM2991 regulator requires an output capacitor to maintain stability. The capacitor must be at least 10 p.F aluminum
electrolytic or 1 p.F solid tantalum. The output capacitor's
ESR must be less than 100, or the zero added to the regulator frequency response by the ESR could reduce the
phase margin, creating oscillations. The shaded area In the
Output Capacitor ESR graph Indicates the recommended
ESR range. An Input capacitor, of at least 1 p.F solid tantalum or 10 p.F aluminum electrolytic, is also needed if the
regulator is situated more than 6 Inches from the Input power supply filter.

g

I

20~--~--~--~--~-,

10

1.0

13

m

MINIMUM LOAD
A minimum load current of SOO p.A is required for proper
operation. The external resistor divider can provide the minimum load, with the resistor from the adjust pin to ground set
to 2.4 kO.

~

0,1

2

0.02

==~;;"';;;;L..;;;;,-=~=;L...--'

0.0

0.25

0.5

0.75

1.0

1.25

OUTPUT CU RRENT (A)
TLlH111260-5

FORCING THE OUTPUT POSITIVE
Due to an Internal clamp circuit, the LM2991 can withstand
positive voltages on its output. If the voltage source pulling
the output positive is DC, the current must be limited to
1.SA. A current over 1.SA fed back Into the LM2991 could
damage the device. The LM2991 output can also withstand
fast positive voltage transients up to 26V, without any current limiting of the source. However, if the transients have a
duration of over 1 ms, the output should be clamped with a
Schottky diode to ground.

SETTING THE OUTPUT VOLTAGE
The output voltage of the LM2991 is set externally by a
resistor divider and the adjust pin current using the following
equation:
VOUT = VREF • (1 + R2/R,) - IADJ • R2
where VREF = - 1.21V. The output voltage can be programmed within the range of -2V to -2SV. The adjust pin
current is about 60 nA, causing a slight error in the output
voltage. However, using resistors lower than 100 kO makes
the adjust pin current negligible. For example, neglecting
the adjust pin current, and setting R2 to 100 kO and VOUT
to -SV, results in an output voltage error of only 0.16%.
ON/OFF PIN
The LM2991 regulator can be turned off by applying a TTL
or CMOS level high signal to the ON/OFF pin (see Current
Sink Application).

2-92

~----------------------------------------------------------------,r

i:

Typical Applications

N

CD
CD

....

Fully Isolated Post-Switcher Regulater
+12V INPUT

+10V
250mA

@

IN5818

I

OUT

+

10s

300

TL/H/11260-6

~National

~ Semiconductor

LP2950/LP2950AC/LP2950C 5V and
LP2951/LP2951 AC/LP2951 C Adjustable
Micropower Voltage Regulators
General Description
The LP2950 and LP2951 are micropower voltage regulators
with very low quiescent current (75 IJA typ.) and very low
dropout voltage (typ. 40 mV at light loads and 380 mV at
100 mAl. They are ideally suited for use in battery-powered
systems. Furthermore, the quiescent current of the
LP2950/LP2951 increases only slightly in dropout, prolonging battery life.
The LP2950 in the popular 3-pin TO-92 package is pin-compatible with older 5V regulators. The 8-lead LP2951 is available in plastic, ceramic dual-in-line, or metal can packages
and offers additional system functions.
One such feature is an error flag output which warns of a
low output voltage, often due to falling batteries on the input. It may be used for a power-on reset. A second feature
is the logic-compatible shutdown input which enables the
regulator to be switched on and off. Also, the part may be
pin-strapped for a 5V output or programmed from 1.24V to
29V with an external pair of resistors.
Careful design of the LP2950/LP2951 has minimized all
contributions to the error budget. This includes a tight initial

tolerance (.5% typ.), extremely good load and line regulation (.05% typ.) and a very low output voltage temperature
coefficient, making the part useful as a low-power voltage
reference.

Features
•
•
•
•
•
•
•
•

High accuracy 5V, guaranteed 100 mA output
Extremely low quiescent current
Low dropout voltage
Extremely tight load and line regulation
Very low temperature coefficient
Use as Regulator or Reference
Needs only 1 p.F for stability
Current and Thermal Limiting

LP2951 versions only
iii Error flag warns of output dropout

101 Logic-controlled electronic shutdown

• Output programmable from 1.24 to 29V

Block Diagram and Typical Applications
LP2950

LP2951

UNREGULATED DC
5V@
S 100 mA

5V@
:S 100 rnA

1.23V
REFERENCE

I
I

I

,

--------------------------_.

I
I
I

TLIH18546-25

._----------I

TLIH18546-1

2-95

o
....

an
~

Connection Diagrams and Ordering Information

a..

...I

.....
~
....
an
Q)

TO-92 Plastic Package (Z)

Dual-tn-Line Packages (N, J)
Surface-Mount Package (M)

OUTPUTBINPUT

N

~

.....
....
an
~

~
o

.....

OUTPUT
SENSE

GND

TLlH/8546-2

2

8

•

7

SHUTDOWN

Bottom View

GROUND

Order Number LP2950ACZ-5.0 or LP2950CZ-5.0
See NS Package Number Z03A

INPUT
FEEDBACK
5V TAP

5

4

ERROR
TLlH/8546-26

Top View

~
~

Order Number LP2951CJ, LP2951ACJ, LP2951J,
LP2951J/883 or 5962-3870501MPA
See NS Package Number J08A

a..

...I

~an

Order Number LP2951ACN or LP2951CN
See NS Package Number N08E
Order Number LP2951ACM or LP2951CM
See NS Package Number M08A

Q)

N

a..

...I

.....
o
an
Q)

N

~

Metal Can Package (H)

Leadless Chip Carrier (E)

INPUT

OUTPUT

INPUT

/

\

10

4
GROUND

GND

11

ERROR
TL/H/8546-24

TLlH/8546-19

Top View

Top View

Order Number LP2951 E/883 or 5962-3870501 M2A
See NS Package Number E20A

Order Number LP2951H, LP2951H/883 or
5962-3870501 MGA
See NS Package Number H08C

2·96

r"g

Absolute Maximum Ratings
If MIlitary/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Power Dissipation
Internally Limited
Lead Temp. (Soldering, 5 seconds)
260'C
Storage Temperature Range
-65' to + 150'C
Operating Junction Temperature Range (Note 8)
LP2951
-55' to + 150'C
LP2950AC/LP2950C,
LP2951AC/LP2951C
-40'to + 125'C

Input Supply Voltage

-0.3 to +30V

Feedback Input Voltage
(Notes 9 and 10)

-1.5to +30V

Shutdown Input Voltage
(Note 9)
Error Comparator Output
Voltage (Note 9)

-0.3 to +30V

-0.3 to +30V

Typ
Output Voltage

TJ = 25'C

5.0

Output Voltage

Output Voltage
(Note 12)
Temperature Coefficient

20

Line Regulation
(Note 14)

6V,;; Vin';; 30V
(Note 15)

0.03

Load Regulation
(Note 14)

100 p.A ,;; IL ,;; 100 mA 0.04

Dropout Voltage
(Note 5)

IL = 100 p.A

o
......

5.025
4.975

5.0

5.025
4.975

5.0

120

20

0.1

0.03

0.1
80
450

5.06
4.94
5.07
4.93

5.1
4.9

V max
Vmin

5.12
4.88

V max
Vmin

150

ppml'C

0.1

IL = 100 p.A

75

120

8

12

0.04

0.1

0.1

50

80

50

450

3BO

120

75

12

B

0.3

0/0 max
0/0 max

150

mVmax
mVmax

600

mVmax
mVmax

140

p.A max
p.A max

14

mAmax
mAmax

200

p.A max
p.A max

220

mAmax
mAmax

450
120

140
8

0/0 max

BO

600
75

0.4
0.2

150
3BO

12

14

Dropout
Ground Current

Vln = 4.5V
IL = 100 p.A

110

Current Limit

You! = 0

160

Thermal Regulation

(Note 13)

0.05

Output Noise,
10 Hz to 100 KHz

CL = 1 p.F

430

430

430

p.Vrms

CL = 200 p.F

160

160

160

p.Vrms

CL = 3.3 p.F
(Bypass = 0.01 p.F
Pins 7 to 1 (LP2951»

100

100

100

p.Vrms

110

170

200
200

160

200

0.05

0.2

1.235

Reference
Voltage

1.235

0.05

0.2

1.235

1.26

1.26
1.22

1.27
1.21

1.2

1.2

1.27
1.19

1.27
1.19

2-97

%/Wmax

LP2951C

1.25

1.26

(Note 7)

200

LP2951AC

1.25
1.22

Reference
Voltage

160

220

LP2951

a·Pln Versions only

170

200

220
0.2

110

CD

....
CJI

Q
r"g

N
CD
CJI

....o

% max

0.2

0.2

14
170

0.04

0.2

140
IL = 100mA

50

CJI

N

V max
Vmin
V max
Vmin

100

....
......

r"g

5.075
4.925

600
Ground
Current

5.05
4.95

Units

5.05
4.95

150
3BO

~

Tested Design
Tested
Tested Design
Limit
Limit
Limit
Typ
Limit
Limit Typ
(Note 3) (Note 4)
(Note 3) (Note 4)
(Notes 3. 16)

0.3

IL=100mA

!Q

LP2950C
LP2951C

LP2950AC
LP2951AC

0.5

50

~
......
N

5.06
4.94
5.075
4.925

100 p.A ,;; IL ,;; 100 mA
TJ';; TJMAX

N
CD

CD
CJI
CI

-25'C ,;; TJ ,;; B5'C
Full Operating
Temperature Range

r"g

r"g

ESD Rating is to be determined.

LP2951
Conditions
(Note 2)

.....
CJI

Electrical Characteristics (Note 1)
Parameter

N
CD
CJI
CI

1.2
1.285
1.185

V max
V max
Vmin
Vmin
V max
Vmin

PI

Electrical Characteristics (Note 1) (Continued)
LP2951AC

LP2951

Conditions

Parameter

(Note 2)

Typ

Tested
Limit

Typ

(Notes 3, 16)

LP2951C

Tested
Limit

Design
Limit

(Note 3)

(Note 4)

Typ

Tested
Limit

Design
Limit

(Note 3)

(Note 4)

Units

a-Pin Versions only (Continued)
Feedback Pin

20

Reference Voltage

40

20

40

60

Bias Current
(Note 12)

20

40

60

60

nAmax
nAmax

20

20

50

ppm/DC

0.1

0.1

0.1

nArC

Temperature Coefficient
Feedback Pin Bias
Current Temperature
Coefficient

Error Comparator
Output Leakage

VOH

=

0.Q1

30V

0.Q1

1

= 4.5V
= 400/LA

Output Low
Voltage

Vin
IOL

Upper Threshold

(Note 6)

150

250

150

250

40

60

40

Lower Threshold
Voltage

(Note 6)

75

Hysteresis

(Note 6)

15

150

250

60

40

400

25

Voltage

1

2

400
60

0.Q1

1

2

Current

25
75

95

95

140

75

/LA max

2

/LA max

400

mVmax
mVmax
mVmin

25

mVmin

140

mVmax
mVmax

95

140
15

15

mV

Shutdown Input
Input

1.3

Logic
Voltage

Low (Regulator ON)
High (Regulator OFF)

Shutdown Pin
Input Current

Vshutdown

=

2.4V

1.3

1.3

0.6
2.0
30

50

0.7
2.0
30

V shutdown

=

30V

450

600

450

600

(Note 11)

3

10

10

/LA max
/LA max
/LA max

750
3

20

100
600

750
3

20

450

V
V max
V min

50

100

750
Regulator Output
Current in Shutdown

30

50

100

0.7
2.0

10

/LA max
/LA max

20

/LA max

Note 1: Boldface limits apply at temperature extremes.
Note 2: Unless otherwise specified all limits guaranteed for TJ = 2S'C, Yin = 6V, IL = 100 p.A and CL = I f'F. Additional conditions for the 8-pin versions are
Feedback tied to SV Tap and Output tied to Output Sense (Vout = 5V) and Vshutdown ,;: 0.8V.
Note 3: Guaranteed and 100% production tested.
Note 4: Guaranteed but not 100% production tested. These limHs are not used to calculate outgoing AQL levels.
Note 5: Dropout Voltage is defined as the input to output differential at which the output vollage drops 100 mV below its nominal value measured at 1V differential.
At very low values of programmed output voltage, the minimum input supply voltage of 2V (2.3V over tempereture) must be taken into account.
Note 6: Comparator thresholds are expressed In terms of a voltage differential at the Feedback terminal below the nominal reference voltage measured at 6V
input. To express these thresholds in terms of output voltage change, multiply by the error amplifier gain = VoutlVref = (RI + R2)/R2. For example, at a
programmed output voltage of 5V, the Error output is guaranteed to go low when the output drops by 95 mV x SVlI.235V = 384 mY. Thresholds remain constant
as a percent of You! as VOU! is varied, with the dropout warning occurring at typically 5% below nominal, 7.S% guaranteed.
Note 7: Vref ,;: Vout ,;: (Vin - IV), 2.3V ,;: Yin ,;: 30V, 100 p.A ,;: IL ,;: 100 mA, TJ ,;: TJMAX.
Note 8: The junction-to-ambient thermal resistance of the TO-92 package is 18O"C/W wHh 0.4' leads and 160"C/W with 0.25' leads to a PC board. The thermal
resistance of the 8-pin DIP packages is 10S'C/W for the molded plastic (N) and 130"C/W for the cerdip (J) lunction to ambient when soldered directly to a PC
board. Thermal resistance for the metal can (H) is 160'C/W junction to ambient and 20"C/W junction to case. Junction to ambient thermal resistance for the 5.0.
(M) package Is 160"C/W. Thermal resistance for the leadless chip carrier (E) package is 9S'C/W junction to ambient and 24'C/W lunction to case.
Note 9: May exceed Input supply voltage.
Note 10: When used in dual-supply systems where the output terminal sees loads returned to a negative supply, the output voltage should be diode-clamped to
ground.
Note 11: Vshutdown ;" 2V, Vln ,;: 30V, Vout = 0, Feedback pin tied to SV Tap.
Note 12: Output or reference voltage tempereture coefficient is defined as the worst case vollage change divided by the total temperature range.
Note 13: Thermal ragulation is defined as the change in output voltage at a time T after a change in power dissipation is applied, excluding load or line regulation
effects. Specifications are for a 50 mA load pulse at VIN = 30V (1.2SW pulse) for T = 10 ms.
Note 14: Regulation is measured at constant junction temperature, using pulse testing with a low duty cycle. Changes in output voltage due to heating effects are
covered under the specification for thermal regulation.
Note 15: Une regulation for the LP29S1 is tested at ISO"C for IL = I mAo For IL = 100 p.A and TJ = 12S'C, line regulation is guaranteed by design to 0.2%. See
Typical Performance Characteristics for line regulation versus temperature and load current.
Note 16: A Military RETS spec is available on request. At time of printing, the LP29S1 RETS spec complied with the boldface limits in this column. The LP2951 H, E,
or J may also be procured as Standard Military Drawing Spec # 5962-3870S01 MGA, M2A, or MPA.

2-98

E;;

Typical Performance Characteristics

N

CD

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Quiescent Current

Dropout Characteristics

10

250

6

J

§

- RL=5DkA

B
~
a;

RL=50A -

0.1

10

1

o

100

I

3

J

I

,

RL=~-

j

75
50

If
123 •

INPUT VOLTAGE (VOLTS)

LOAD CURRENT (mA)

"'CI

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o
o

5

r-

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225
200
175
150
125
100

25

o

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Input Current

5

1--

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INPUT VOLTAGE (VOLTS)

o

r-

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Output Voltage vs.
Temperature of 3
Representative Units

Input Current
120
110
100

!

I
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a;

RL=50ll- -

90

80
70
60

,

so
40

,

III
~
~

5

5

30

oI.9B

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0.2l1

f

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4 5 6 7 8 9 10

so

75 100 125 ISO

CD

120

~

100

BD

!Z

60

~
a

40

tl

•

0

1 2 3

J
~
i3

-

5.0

oI.9B

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140

5.D2

20
10

I

Quiescent Current

20

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.....

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012345678

INPUT VOLTAGE (VOLTS)

Quiescent Current

Quiescent Current

10

/--..

100

80

J.
VIN=6V_

i" i'--

I- -

..... l- I-

70

,/

,.

VIN =6V- - \.=IOOmA_

IL= IOO 11A

I'-

......

I L =100mA

:>

a

60

so

-75-SO-25 0 25 50 75 100 1251SO

7
-75 -SO-25 0 25 SO 75 100 125 ISO

TEMPERATURE (OC)

TEMPERATURE (OC)

170

!

160

IS

ISO

~

140

I
l!ijli

Short Circuit Current

......

~

600

r-

V

•

1
III
~
~

130

5

I

120
110
100
-75 -50-25 0 25 SO 75 100 1251SO

TEMPERATURE (OC)

J

012345678

INPUT VOLTAGE (V)

Dropout Voltage

500

Dropout Voltage

J.,..-

SOD

400
300

o

L'"

i-'"

,

~~I~

100
50

iLrr

1-'1-'--

-f- ~

o

-75 -SO -25 0 25 SO 75 100 125 ISO

TEMPERATURE (OC)

OUTPUT CURRENT
TL/H/8546-3

2·99

CI'I
.....
~
.....

r-

IL=O

110

90

ILU'A

I
I

TEMPERATURE (OC)

120

r-

160

INPUT VOLTAGE (VOLTS)

~

CI'I

5.D4

~

.....
.....

Quiescent Current

5.D6

o

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Typical Performance Characteristics

LP2951
Feedback Bias Current

LP2951
Minimum Operating Voltage
2.2

E

2.1

~

2.0

;

IS

~

1.8

~

I

(Continued)

20
10

\
~ ......

1.6

-75

-so -25

:!

!
...... r-.,

I.

......

:;

-10

./

t!,!

1.7

-20

I

-250 "'-':':"-.....L----JL---'-.....L----J
-2.0 -1.5 -1.0 -0.5 0
0.5 1.0

TEltPERATURE (OC)

LP2951
Error Comparator Output
2.5

TJ.'2~"C

VOUT =5V
2.0

r--

I

FEEDBACK VOLTAGE (V)

LP2951
Comparator Sink Current

8

-

I -: f---h..-F'~<-+--+--l

-30
-75 -50-25 0 25 50 75 100 125150

0 2S 50 75 100 125 150

TEltPERATURE (OC)

V

/

1.5

H~ESiS-

T1Joc

1//

1.0

1I

TA=-55OC

J

I
-2

LP2951
Feedback Pin Current

0.5

~
0.0 ~

NilE: PULlUP RESISTOtroSEPARAlE 5V SUPPLY

I I os

Line Transient Response
I~V

l!l!j~

50

151ll~ U\r
~z

mV

0

IN

slil

V

>
4V

60

lil2 '5O

lils
~
!j E 2D

~..sI00

I- f~.:.'''F

I"\,

7

~!; 0

50

"l

~~-20
o -40

5~
0
o -so
CL=I"F-

-100

<;'=10"F IVOUT =5V _
fI

-80

VOUT=15;'~+
I

12

4

Output Impedance

I

i~

iE

.:!l.

1Or--+--"--r--+~~

I :r--+--~~~~~n

02
0.1
GIll

~

30

D.1I2

CL=II'F

VIH=6V-+__+----II---I
VOUT =5V

0.D1
ICIO

lK

10K

fREQUENCY (Hz)

-I

lOOK

111

20 '0'

102

101

10'

FREQUENCY (Hz)

'L = 10mA
V,N =8VVOUT =5V <;'=10"F

/

r--~

-100 0 100 200 300 400 500 600 700
TIME (po)

Ripple Rejection
110

1IOb::±~~~--~~
'iii'

1
05

10

f-

I
I
I

-2

Ripple Rejection

2

800

I; !

IIO~~--~--r-~--,

10
5

I

20

1

TIME (mo)

TIME (ma)

I

16

600

LP2951
Enable Transient

80

200

400

TIME (PI)

Load Transient Response

250

sill

200

OUTPUT LOW VOLTAGE (V)

Load Transient Response

<;'=lji1'
'L=lmA
UT 5V

i

f-

~g IN

0.00.1 02 D.3 D.4 0.5 D.6 0.7 D.6
INPUT VOLTAGE (V)

" i I-

110

'iii'

.:!l.

I
~

10

110
50
~

30
20 '0'

102

FREQUENCY (Hz)
TL/H/B54B-4

2·100

r-

Typical Performance Characteristics

"tI
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(Continued)

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U1

Ripple Rejection

Output Noise

LP2951 Divider Resistance

!II

70

;;;~

400
IL=50mA

!II IL=IOOmA ~

z

§

50

:il

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~

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t:l

Ct.=II'F
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101

102

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300

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20
10

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105

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FREQUENCY (Hz)

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Shutdown Threshold Voltage

120

25

20

1.6

I,

11..

1.2

ID

REGULATOR

-

15
10 TJ =150OC....

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5

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7

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......

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0 25 50 75 100 125 150

5

10

15

20

25

__

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30

LP2950 Maximum
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L-~

10

INPUT VOLTAGE (V)

TEMPERATURE (OC)

120

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0.6
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U1

LP2951 Maximum
Rated Output Current

Line Regulation

30

15

__

L-~~

20

25

30

U1

......

o

INPUT VOLTAGE (V)

Thermal Response

.--,--,--;--r-,--,

I'r-.

",,-

I

1--.

1.2fW

1--1--1--

20
OL-~

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~~

10

15

__

~-L~

20

25

30

10

INPUT VOLTAGE (V)

20
TIME

30

50

<1'.)
TL/H/B546-5

Application Hints
runs the error amplifier at lower gains so that more output
capacitance is needed. For the worst-case situation of a
100 mA load at 1.23V output (Output shorted to Feedback)
a 3.3 ,...F (or greater) capaCitor should be used.
Unlike many other regulators, the LP2950 will remain stable
and in regulation with no load in addition to the internal voltage divider. This is especially important in CMOS RAM
keep-alive applications. When setting the output voltage of
the LP2951 version with external resistors, a minimum load
of 1 ,...A is recommended.
A 1 JLF tantalum or aluminum electrolytic capacitor should
be placed from the LP2950/LP2951 input to ground if there
is more than 10 inches of wire between the input and the AC
filter capacitor or if a battery is used as the input.

EXTERNAL CAPACITORS
A 1.0 ,...F (or greater) capaCitor is required between the
LP2950/LP2951 output and ground for stability. Without this
capacitor the part will oscillate. Most types of tantalum or
aluminum electrolytics work fine here; even film types work
but are not recommended for reasons of cost. Many aluminum electrolytics have electrolytes that freeze at about
-30·C, so solid tantalums are recommended for operation
below -25·C. The important parameters of the capacitor
are an ESR of about 5 n or less and a resonant frequency
above 500 kHz. The value of this capacitor may be increased without limit.
At lower values of output current, less output capaCitance is
required for stability. The capacitor can be reduced to
0.33 ,...F for currents below 10 rnA or 0.1 JLF for currents
below 1 rnA. USing the S-Pin versions at voltages below 5V

Stray capacitance to the LP2951 Feedback terminal (pin 7)
can cause instability. This may especially be a problem
2-101

fI

0.----------------------------------------------------------------------.
...
In

g
....
~

...

Application Hints (Continued)

when using high value external resistors to set the output
voltage. Adding a 100 pF capacitor between Output and
Feedback and increasing the output capacitor to at least
3.3 /IoF will fix this problem.

In

ERROR DETECTION COMPARATOR OUTPUT

a.

The comparator produces a logic low output whenever the
LP2951 output falls out of regulation by more than approximately 5%. This figure is the comparator's built-in offset of
about 60 mV divided by the 1.235 reference voltage. (Refer
to the block diagram in the front of the datasheet.) This trip
level remains "5% below normal" regardless of the programmed output voltage of the 2951. For example, the error
flag trip level is typically 4.75V for a 5V output or 11.4V for a
12V output. The out of regulation condition may be due either to low input voltage, current limiting, or thermal limiting.

~

.......I...

In

~

....~
(.)
C)

In

m

~

~
m

C"I

a.

...I

~
~

a.

...I

The complete equation for the output voltage is
VOUT = VREF· ( 1

+ :~) + IFBR,

where VREF is the nominal 1.235 reference voltage and IFB
is the feedback pin bias current, nominally - 20 nA. The
minimum recommended load current of 1 iJ-A forces an upper limit of 1.2 MO on the value of R2, if the regulator must
work with no load (a condition often found in CMOS in
standby). IFB will produce a 2% typical error in VOUT which
may be eliminated at room temperature by trimming R,. For
better accuracy, chOOSing R2 = 1OOk reduces this error to
0.170/0 while increasing the resistor program current to
12 iJ-A. Since the LP2951 typically draws 60 iJ-A at no load
with Pin 2 open-circuited, this is a small price to pay.
REDUCING OUTPUT NOISE

Figure 1 below gives a timing diagram depicting the ERROR

In reference applications it may be advantageous to reduce
the AC noise present at the output. One method is to reduce
the regulator bandwidth by increasing the size of the output
capaCitor. This is the only way noise can be reduced on the
3 lead LP2950 but is relatively inefficient, as increasing the
capaCitor from 1 iJ-F to 220 iJ-F only decreases the noise
from 430 iJ-V to 160 iJ-V rms for a 100 kHz bandwidth at 5V
output.

signal and the regulated output voltage as the LP2951 input
is ramped up and down. The ERROR signal becomes valid
(low) at about 1.3V input. It goes high at about 5V input (the
input voltage at which VOUT = 4.75). Since the LP2951's
dropout voltage is load-dependent (see curve in typical performance characteristics), the Input voltage trip pOint (about
5V) will vary with the load current. The output voltage trip
point (approx. 4.75V) does not vary with load.

Noise can be reduced fourfold by a bypass capaCitor accross R1, since it reduces the high frequency gain from 4 to
unity. Pick

The error comparator has an open-collector output which
requires an external pullup resistor. This resistor may be
returned to the 5V output or some other supply voltage depending on system requirements. In determining a value for
this resistor, note that while the output is rated to sink
400 iJ-A, this sink current adds to battery drain in a low battery condition. Suggested values range from 100k to 1 MO.
The resistor is not required if this output is unused.

1
CSYPASS "" 21TR, .200 Hz
or about 0.01 iJ-F. When doing this, the output capaCitor
must be increased to 3.3 iJ-F to maintain stability. These
changes reduce the output noise from 430 iJ-V to 100 iJ-V
rms for a 100 kHz bandwidth at 5V output. With the bypass
capacitor added, noise no longer scales with output voltage
so that improvements are more dramatic at higher output
voltages.

PROGRAMMING THE OUTPUT VOLTAGE (LP2951)
The LP2951 may be pin-strapped for 5V using its internal
voltage divider by tying Pin 1 (output) to Pin 2 (sense) and
Pin 7 (feedback) to Pin 6 (5V Tap). Alternatively, it may be
programmed for any output voltage between its 1.235V reference and its 30V maximum rating. As seen in Figure 2, an
external pair of resistors is required.

L.::.._.,

lDD;;;K_ _

V~~~~~~
----1 I
r----

.;E;RR:;OR::"....~=-I ERROR

+VIN

OUTPUT

LP2951
•• SHUTDOWN 3 SO
INPUT

ERROR·

INPUT

VOLTAGE
TL/H/8546-7

TL/H/8546-20

FIGURE 2. Adjustable Regulator

'When VIN " 1.3V, the error flag pin becomes a high Impedance, and the
error flag voltage rises to its pull·up voltage. Using VOUT as the pull·up
voltage (see Figuf9 2), rather than an external 5V source, will keep the error
flag voltage under 1.2V (typ.) in this condition. The user may wish to divide
down the error flag voltage using equal·value resistors (10 kO suggested), to
ensure a low-level logic signal during any fault condHion, while stili allowing a
valid high logic level during normal operation.

'See Application Hints
Vout=VRe,(1

+~)

"Drive with TTL·high to shut down. Ground or leave open if shutdown feature is not to be used.

FIGURE 1, ERROR Output Timing

Note: Pins 2 and 6 are left open.

2-102

r-

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Typical Applications

N

~

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1A Regulator with 1.2V Dropout

r-

---t---.. . ----.

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UNREGULATED - -......
INPUT

N

I

OUTPUT

t=-_ _....._.5V:t 1%@

r-

OT01A

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r-

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~
.....
.....

TLlH/8546-22

r-

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300 mA Regulator with 0.75V Dropout
UNREGULATED-.....-------------~....INPUT

Wide Input Voltage Range Current
Limiter

...

+VIN

2N5432
(2)

B

.....
Q
:J>

r-

"'tI

+VIN

N
CO
U'I

..,E:;,RR:;O:;:,R=--=-I ERROR

r---....- -...-+~~TPUT

N
CO
U'I

OUTPUT

.....

o

LP2951
SHUTDOWN 3 SO
INPUT

TL/H/8546-21
TL/H/8548-9

-Minimum input~output voltage ranges from
40 mV to 400 mY. depending on load current.
Current limit is typically 160 rnA.

Low Drift Current Source
+V=2-+30V

.__ L.
I

I

Id:

LOAD:

I

I

--

IL= 1.:3

5 Volt Current Limiter
5V BUS

8

+VIN

•

LP2950Z
'Vour Rl5V
Vour!--t--

VOUT

LP2951
SHUTDOWN 3 SO
INPUT
GND

GND

4
TL/H/8546-10

'Minimum Input-output voltage ranges from 40 mV to 400 mY. depending on
load current. Current limit is typically 160 mAo

R
1%

TL/H/8546-8

2·103

Typical Applications (Continued)

2 Ampere Low Dropout Regulator
CURRENT
LIMIT SECTION

Regulator with Early Warning
and Auxiliary Output

~

0.05

470
VOUT

5V TAP

7

rB

MJE2955

V+

+

+VIN

I'P'1=,."

GNO

220

I

20ko.

EARLY WARNING

OJ

+
100

L-~_ _V'T0ur~

R2

.033:

330kll

r

VOUT

+~)

TL/H/8546-t3

For 5Vouto use internal resistors. Wire pin 6 to 7, & wire pin 2 to

I'P

LP2951
#2

I

You. = 1.23V ( 1

RESET

+VIN

+ Vout Buss.

5V Regulator with 2.5V Sleep Function

VOO

+VIN

+

EiiRoR

SO

4.7

t - - - -.. l~ ]!ANT·II'F

I:
-

3

FB

I

03

5V TAP

Rt +

t---p--r'''ISD

27kll

rB

ERROR
FLAG

ERROR

LP2951

NICAO

4

+Vour @2A

10ko.

20

LP2951
#1
ERROR

• SLEEP
INPUT

p

GNO

4

,

47kll
8
TLlH/8546-tt

-,:E~RR=OR~~5"i ERROR

• Early waming flag on low input voltage

+VIN

OUTPUT

• Main output latches off at lower input voltages

LP2951

• Battery backup on auxiliary output

SHUTDOWN 3 SO
INPUT

Operation: Reg. # l's You! is programmed one diode drop above 5V. lis error
flag becomes active when Yin ,;; 5.7V. When Vln drops below 5.3V, the error
flag of Reg. #2 becomes active and via 01 latches the main output off.
When Vin again excaeds 5.7V Reg. # 1 is back in regulation and the early
waming signal rises, unlatching Reg. # 2 via 03.

Latch Off When Error Flag Occurs
+Vln

'High input lowers Vou• to 2.5V

TLlH/8546-t4

Open Circuit Detector for
4 20 rnA Current Loop
+5V

VOUT

VOUT

4.7kll

4--20mA
RI

rB
RESET
R2

r¢

OUTPUT"

+

IN
4001

Vour
LP2951

TL/H/8546-t2

" HIGH FOR
IL<3.5mA
360

MIN. VOLTAGE0l4V

2·104

TL/H/8546-t5

r-

Typical Applications

"tI

N
CD
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(Continued)

~
r-

Regulator with State-of-Charge Indicator

"tI

39kD.

RESET

5

+VIN
ERROR

~r-

+VOUT =5V
VOUT

SO

I
+

LP2951
3

m

FB

7

6

1}LF

~

U\

o

~
r-

"tI

m

+

6V
~ LEAD-AaD
.lBAnER\'

....
.....

lOOk.!!.

r-

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 1250)

8.2kn

TL/H/8546-18

LM34 for 12S'F Shutdown
LM3S for 12S'C Shutdown

2·106

(/)
IN

()

::T

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3

£II

n'
c

iii'

CQ

Dl

R27
182 kJl

,I

1

1

3

ISVTAP

R28
60kJl

~
~
R30
30kJl
50kJl

4

13kJl

~ .~~~ ~

- - - - DENOTES CONNECTION ON

L--....J.

LP2950 ONLY

A__

I ,

6

,

'I

GND

TUH/B546-23

:>~S6~d' 1:>"~S6~d' I~S6~d' I:>OS6~d' 1:>"OS6~d' IOS6~d'

~National

~ Semiconductor

LP2952/LP2952A/LP2953/LP2953A
Adjustable Micropower Low-Dropout Voltage Regulators
General Description

Features

The LP2952 and LP2953 are micropower voltage regulators
with very low quiescent current (130 /LA typical at 1 mA
load) and very low dropout voltage (typ. 60 mV at light load
and 470 mV at 250 mA load current). They are ideally suited
for battery-powered systems. Furthermore, the quiescent
current increases only slightly at dropout, which prolongs
battery life.

•
•
•
•
•
•
•
•
•

The LP2952 and LP2953 retain all the desirable characteristics of the LP2951, but offer increased output current, additional features, and an improved shutdown function.
The internal crowbar pulls the output down quickly when the
shutdown is activated.
The error flag goes low if the output voltage drops out of
regulation.

Output voltage adjusts from 1.23V to 29V
Guaranteed 250 mA output current
Extremely low quiescent current
Low dropout voltage
Extremely tight line and load regulation
Very low temperature coefficient
Current and thermal limiting
Reverse battery protection
50 mA (typical) output pulldown crowbar

LP2953 Versions Only
• Auxiliary comparator included with CMOS/TIL compatible output levels. Can be used for fault detection, low
input line detection, etc.

Reverse battery protection is provided.
The internal voltage reference is made available for external
use, providing a low-T.C. reference with very good line and
load regulation.
The parts are available in plastic DIP and surface mount
packages.

Applications
•
•
•
•

High-efficiency linear regulator
Regulator with under-voltage shutdown
Low dropout battery-powered regulator
Snap-ON/Snap-OFF regulator

Block Diagrams
LP2952

LP2953

t ____________________ _
TL/H/11127-1

2-108

TLlH/11127-2

r-

."

Absolute Maximum Ratings

N

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.

Lead Temp. (Soldering, 5 seconds)

260'C
Internally Limited
-20Vto +30V

Power Dissipation (Note 2)
Input Supply Voltage

Storage Temperature Range
-65'Cto + 150'C
Operating Junction Temperature Range
LP2952AIILP29521
-40'C to + 125'C
LP2953AI/LP29531
-40'C to + 125'C

-0.3Vto +5V

Feedback Input Voltage (Note 3)
Comparator Input Voltage (Note 4)
Shutdown Input Voltage (Note 4)
Comparator Output Voltage (Note 4)

-0.3Vto +30V
-0.3Vto +30V

CD
CI1

N
......

r-

."
N
CD
CI1
N

~
r-

-0.3Vto +30V

."

2kV

CD
CI1

ESD Rating (Note 15)

N

Co)

......
r-

Electrical Characteristics Limits in standard typeface are for TJ = 25'C, bold typeface applies over the
-40'C to + 125'C junction temperature range. Limits are guaranteed by production testing or correlation techniques using
standard Statistical Quality Control (SQC) methods. Unless otherwise specified: VIN = 6V, IL = 1 mA, CL = 2.2 /LF, Feedback
pin is tied to 5V Tap pin, Output pin is tied to Output Sense pin, Your = 5V.

Symbol

Parameter

Conditions

2952AI
2953AI

Typical
Min

Va

Output Voltage

5.0
1 mA :s; IL :s; 250 mA

tNo
AT
AVo
Va
AVo
Va
VIN-VO

Output Voltage
Temp. Coefficient

(Note 5)

Output Voltage
Line Regulation

VIN

Output Voltage
Load Regulation
(Note 6)

IL
IL

=
=

1 mA to 250 mA
0.1 mA to 1 mA

Dropout Voltage
(Note 7)

IL

=

1 mA

IL

IGND

Ground Pin Current
(Note 8)

50mA

=

100mA

IL

=

250 mA

IL

IL
IL

IGND

6V to 30V

IL

IL

IGND

=

=

=
=
=
=

1 mA
50mA
100mA
250mA

Ground Pin Current
at Dropout (Note 8)

VIN = 4.5V
IL = 100/LA

Ground Pin Current
at Shutdown (Note 8)

(Note 9)

5.0

20
0.03
0.04

60
240
310
470
130
1.1
4.5
21
165
105

2-109

29521
29531
Max

Min

N

CD
CI1

Co)

:r>

Units
Max

4.975

5.025

4.950

5.050

4.940

5.060

4.900

5.100

4.930

5.070

4.880

5.120

100

."

150

0.1

0.2

0.2

0.4

0.16

0.20

0.20

0.30

100

100

150

150

300

300

420

420

400

400

520

520

600

600

800

800

170

170

200

200

2

2

2.5

2.5

6

6

8

8

28
33

33

V

ppml'C
%
%

mV

/LA

mA

28

210

210

240

240

140

140

p.A
/LA

•

Electrical Characteristics Limits in standard typeface are for TJ =

25'C, bold typeface applies over the
-40'C to + 125'C junction temperature range. Limits are guaranteed by production testing or correlation techniques using
standard Statistical Quality Control (SQC) methods. Unless otherwise specified: VIN = 6V, IL = 1 rnA, CL = 2.2 /loF, Feedback
pin is tied to 5V Tap pin, Output pin is tied to Output Sense pin, VOUT = 5V. (Continued) .

29521
29531

2952AI

Symbol

Parameter

Conditions

2953AI

Typical
Min

ILiMIT

Current Limit

VOUT = 0

380

!:"vo
aPd

Thermal Regulation

(Note 10)

en

Output Noise Voltage
(10 Hz to 100 kHz)
IL=100mA

CL = 2.2/loF

400

CL=33/loF

260

CL = 33 /loF (Note 11)

80

VREF

Reference Voltage

(Note 12)

Reference Voltage
Line Regulation

VIN = 2.5V to 6V
VIN = 6V to 30V
(Note 13)

Reference Voltage
Load Regulation

IREF = 0 to 200 /loA

VREF
aVREF
aT

Reference Voltage
Temp. Coefficient

(Note 5)

IB(FB)

Feedback Pin
Bias Current

aVREF
VREF
aVREF

10
(SINK)

Output "OFF"
Pulldown Current

0.05

1.230

Min

Units
Max

500

500

530

530

0.2

0.2

1.215

1.245

1.205

1.255

1.205

1.255

1.190

1.270

0.03

0.25

0.1

0.2

0.2

0.4

0.4

0.8

0.6

1.0

20

50

rnA

%/W

/loVRMS

V

%

%
ppml'C

20
(Note 9)

Max

40

40

60

60

30

30

20

20

nA
rnA

DROPOUT DETECTION COMPARATOR
Output "HIGH"
Leakage

VOH = 30V

Output "LOW"
Voltage

VIN = 4V
10(COMP) = 400/loA

VTHR
(MAX)

Upper Threshold
Voltage

(Note 14)

VTHR
(MIN)

Lower Threshold
Voltage

(Note 14)

HYST

Hysteresis

(Note 14)

10H
VOL

0.Q1
150
-240
-350

1

1

2

2

250

250

400

400

-320

-150

-320

-150

-380

-100

-380

-100

-450

-230

-450

-230

-640

-160

-640

-160

60

/loA
mV
mV
mV
mV

SHUTDOWN INPUT (Note 16)
Vos

Input Offset Voltage

HYST

Hysteresis

IB

Input Bias Current

(Referred to VREF)

±3

-7.5

7.5

-7.5

7.5

-10

10

-10

10

-30

30

-30

30

-50

50

-50

50

6
VIN(S/D) = 0 to 5V

10

2·110

mV
mV
nA

Electrical Characteristics Limits in standard typeface are for TJ = 25'C, bold typeface applies over the
-40'C to

+ 125'C junction temperature range. Limits are guaranteed by production testing or correlation techniques using
=

standard Statistical Quality Control (SQC) methods. Unless otherwise specified: VIN
6V, IL
pin is tied to 5V Tap pin, Output pin is tied to Output Sense pin, VOUT
5V. (Continued)

=

1 mA, CL

= 2.2/LF, Feedback

=

Symbol

Parameter

Conditions

Typical

2952AI

29521

2953AI

29531

Min

Max

Units

Min

Max

AUXILIARY COMPARATOR (LP2953 Only)
Vos

Input Offset Voltage

HYST

Hysteresis

Is

Input Bias Current

IOH

Output "HIGH" Leakage

(Referred to VREF)

±3

Output "LOW" Voltage

7.5

-7.5

7.5

10

-10

10

-30

30

-30

30

-50

50

-50

50

6
VIN(COMP)

VOH

= 0 to 5V

= 30V

= 1.3V
VIN(COMP) = 1.1V
lo(COMP) = 400 /LA
VIN(COMP)

VOL

-7.5

-10

10

mV
mV

0.01

150

1

1

2

2

250

250

400

400

nA

/LA

mV

Note 1: Absolute maximum ratings indicate limits beyond which damage to the component may occur. Electrical specifications do not apply when operating the
device outside of Its rated operating conditions.

Nole 2: The maximum allowable power dissipation is a function of the maximum junction temperature, TJ{MAX), the junction-ta-ambient thermal resistance, BJ_A,
and the ambient temperature, TAo The maximum allowable power dissipation at any ambient temperature is calculated using: P (MAX) = TJ(MAX) - TA.
8J-A

Exceeding the maximum allowable power dissipation will cause excessive die temperature, and the regulator will go into thermal shutdown. See APPLICATION
HINTS for additional information on heatsinking and thermal resistance.
Note 3: When used in dual-supply systems where the regulator load is returned to a negative supply, the output voltage must be diode·clamped to ground.
Note 4! May exceed the input supply voltage.
Note 5: Output or reference voltage temperature coefficient is defined as the worst case voltage change divided by the total temperature range.
Note 6: Load regulation is measured at constant junction temperature using low duty cycle pulse testing. Two separate tests are performed, one for the range of
100 !LA to 1 rnA and one for the 1 rnA to 250 rnA range. Changes in output voltage due to heating effects are covered by the thermal regulation specification.

Nota 7: Dropout voltage is defined as the input to output differential at which the output voltage drops 100 mV below the value measured with a 1 volt differential.
At very low values of programmed output voltage, the input voltage minimum of 2V (2.3V over temperature) must be observed.
Note 8: Ground pin current is the regulator quiescent current. The total current drawn from the source is the sum of the ground pin current, output load current, and
current through the external resistive divider (if used).

Nole 9: VSHUTDOWN " l.tv, VOUT = 5V.
Nola 10: Thermal regulation is the change in output voltage at a time T after a change in power diSSipation, excluding load or line regulation effects. Specifications
are for a 200 rnA load pulse at VIN = 20V (3W pulse) for T = 10 ms.
Note 11: Connect a 0.1 fLF capacitor from the output to the feedback pin.
Note 12: VREF " VOUT " (VIN - tv), 2.3V " VIN " 30V, 100 fLA " IL " 250 rnA.
Nota 13: Two separate tests are performed, one covering 2.5V " VIN " 6V and the other test for 6V " VIN " 30V.
Note 14: Comparator thresholds are referred to a 5V output. To express the threshold voltages in terms of a differential at the Feedback terminal, divide by the
error amplifier gain = Vour/VREF.
Note 15: Human body model, 200 pF discharged through 1.5 kO.
Note 16: Drive Shutdown pin with TTL or CMOS·low level to shut regulator OFF, high level to turn regulator ON.

2-111

•

Typical Performance Characteristics
Quiescent Current
200
180

'<
.3
!Z

!il

~

160
140

-

Quiescent Current
1

'L

~ 10ciPA

120

i:l

100

ii':
~
~

80
40

'<
.3

150

!

140

0

120

"~

110

'" ....... ......

130

ii':

I
I

60

z

20
2

4

5

100
-75 -50 -25 0

6

16

iii

14

IL :: 250mA

i:l
z
a:

10

::i

-........

12

]:

!
z

a:

0

z

0

"~
0

0

20

l- I-

IS

IL

= 250mA

10

lL :: 100mA

-75 -so -25 0

10

90

Ripple Rejection
80

/

~

~

z

70

.\

60

J).

\

50
40

= 2.2pF

!
.~

-"y

0.1

10

100

60

Ripple Rejection

VIN

30

IL :: 100mA

~ 6V

0.01

~

1\

'\... /

0.1

W

10

100

\\

50
YIN:: 6Y

40
30

rIL=oLI"

60

Your = 5V

c,. = 2.2pf

-,y

J¥ ~iOOPA
I

20
1000

0.01

0.1

10

100

1000

fREQUENCY (KHz)

Line Transient Response

f-f-t-t-+-+-+ CL = 33pF
~ '>
f-t-t-t-+-+-+ Il = 10 rnA
~..s. 40 f-t-t-+-+-+-+ VOlJT:: 5V

S~

0

f-f-M'If'4-t-+f\lr-++-I

-40

H-++++-H-++-I

~ ~ 6Y
0.6

.~

J\
\

Output Impedance
100

80

~~

TIME (ms)

70

FREQUENCY (KHz)

Your = Sy

0.4

z

J

~l:iBV1'---\-+++++-+-+-+-l
~~
0.2

80

!

r-.\
\\

Your = 5V
CL = 2.2p.F

:;;~

10

1000

Cl :: 2.2J.'F
IL :: lOrnA

V

90

./'\

........... """,1\

40

Line Transient Response

1\

l'-....

Il :: 250mA

FREQUENCY (KHz)

1000

100

50

20

\ / ' IL =10mA

20
0.01

r

,%/

"

Your :: 5V
CL

'L=lmA /

\\

VIN = BY

~

70

100

LOAD CURRENT (rnA)

90

80

30

25 50 75 100 125 150

JUNCTION TEMPERATURE (00)

Ripple Rejection

f!!

-

o
6

100

!

~

......

"
~

INPUT VOLTAGE (V)

z

Output Noise Voltage

z

o
o

!

OUTPUT CURRENT (rnA)

Ground Pin Current
25

1
'1..1

I.

25 50 75 100 125 150

TEMPERATURE (OC)

Ground Pin Current
20

......

'L ='~A

INPUT VOLTAGE (V)

'<
.!!.

r-....

0

o
o

Ground Pi", Current vs Load

160

g

10

I
l!!

S

~

0.1

f-f-t-+--+--+-+-+++-I

0.8

0.1
TIME (ms)

10

100

1000

FREQUENCY (KHz)

TL/H/11127-3

2-112

Typical Performance Characteristics
Load Transient Response
BOO

...

""'I.

400

!oI;~.!.

-~ r-

> ...

sri
~:i!

-400

'"

-BOO

Load Transient Response

.,....

""'-~

....

V,N = 6V
Vour 'lII 5V

.......

0

~

G. = 331'F

0

'L = IOOI'A

\. = 250mA

0

=>u

~~u=>

Dropout Characteristics

20 0

V,N = 6V
VOUT = 5V

G. = 2.2;:;-

(Continued)

-20

~ 250m~

250"",

'"

IOOI'A

9 u~
B

12

16

1

100",A
O~~~~~~~~.J

20

10

20

TIME (m.)

30

40

o

aD

50

2

Enable Transient

3

4

INPUT VOLTAGE (v)

TIME (m.)

Short-Circuit Output Current
and Maximum Output Current

Enable Transient

aoor-~~~-r~-r~~-'

0

a

c,. .2.2I'F

5S0~~-t-~~~~~~---t

J

C1. -2.2}JF

II c,. ·!3I'F

..IVOUT •

c,..UpF 1--'VOUT • 5V
~ = 10 rnA
Y,N • 14V

--

~

SV ' • 10 rnA

V,N • BV

-

250 I--l-~:;::-T""+-+-+--H

2

3

200 '--'--'--'--J....J....-'--'--'---'
-75 -50 -25 0 25 50 75 100125150

3

TIME (m.)

TIME (m.)

Feedback Bias Current

JUNCTION TEMPERATURE (Oc)

Feedback Pin Current

Error Output

20
VOUT = 5V

~

10

'<

.:.

itl
~

/

-10
-20

-u~

I
-

-1001--t..,.."'P""'1f--1--t--j
-150

FEEDBACK VOLTAGE (V)

TEMPERATURE (Oc)

Comparator Sink Current
2.5
T.J

-5

2.0

§

1.5

tl

1.0

V1//

J

'"

z
;;;
0.5
0.0

.).(1

i'"

Dropout Detection
Comparator Threshold Voltages
~

12~OC
./

>In

TA =-55°C

~

1 1

II

0.00.1 0.2 0.3 0.4 0.5 0.6 0.7 O.B 0.9
OUTPUT LOW VOLT AGE (V)

~

./
200

r----

NrE: PULLUP RESISTOR TO
SEPARATE 5V SUPPLY

INPUT VOLTAGE (V)

Divider Resistance

J1

J

r----2

-250 Lo""::"_.L........L_...l....""'!_.J
-2.0 -1.5 -1.0 -0.5
0.5 1.0

I---

HylTERESls-+

8'"

-200 ~7f-+--+-+--l--l

-30
-75-50-250 255075100125150

'<

F--l"c.-*'.--:::t=!::---l---1

I

I---

~
'"
~
::

-50 1--+--+----1b!f1f--t----t

~
~ I-"'"

;~
"' ....
!j ~
"'0

9:i
",=>

~~

!e

-700
-600
-500

LOWER THRESHOLD

.....

-400
-300

~ ~ -200

100

l- I- -

:.-

.. 15

tL

-

UPPER THRESHOLD

~ ~ -100

o

8

-75-50-250

255075100125150

TEMPERATURE (OC)

-0
-75-50-250

25 SO 75100125150

TEMPERATURE (OC)
TL/H111127-4

2-113

Typical Performance Characteristics

(Continued)

Thermal Regulation

Minimum Operating Voltage
2J

~s

'-'.5
~I!I

U

0

15
10

oS

v

t..-'

£

-

III

2.2

;!

.

.....

g
~~
f ..

~

2.1

~~

2.0

II-

~

REFERENCE AND REGUlATOR
(REGULAlOR OUTPUT = 1.2lV)

..... .....

1.9

2

=>

;!!

~

~

10

20

lB

1.7
-75

30

-so -25

--

0 25 50 75 100 125 150

TEIIPERAlURE C'C)

TIME (m.)

TL/H/11127 -5

Schematic Diagram

TUH/11127-6

2-114

r

"U
~
CD

Application Hints
Figure 2 shows copper patterns which may be used to dissipate heat from the LP2952 and LP2953:

HEATSINK REQUIREMENTS
A heatsink may be required with the LP2952/LP2953 depending on the maximum power dissipation and maximum
ambient temperature of the application. Under all possible
operating conditions, the junction temperature must be within the range specified under Absolute Maximum Ratings.
To determine if a heatsink is required, the maximum power
dissipated by the regulator, P(max), must be calculated. It is
important to remember that if the regulator is powered from
a transformer connected to the AC line, the maximum
specified AC input voltage must be used (since this produces the maximum DC input voltage to the regulator). Figure 1 shows the voltages and currents which are present in
the circuit. The formula for calculating the power dissipated
in the regulator is also shown in Figure 1:

~

U1

~
.....
r
"U
~

CD

U1
(0)

......
r

"U

~

CD

U1

(0)

:J>

TLlH/11127-7

+ (VIN) IG

TL/H/11127-8

FIGURE 1. Current/Voltage Diagram

·For best results, use L

= 2H

"14-Pin DIP is similar. refer to Table I for pins designated for heatsinking.

FIGURE 2. Copper Heatslnk Patterns

The next parameter which must be calculated is the maximum allowable temperature rise, T R(max). This is calculated by using the formula:
TR(max) = TJ(max) - TA(max)

Table II shows some values of junction-to-ambient thermal
resistance (OJ-AI for values of Land W for 1 oz. copper:
TABLE II

where: TJ(max) is the maximum allowable junction temperature
TA(max) is the maximum ambient temperature
Using the calculated values for T R(max) and P(max), the
required value for junction-to-ambient thermal resistance,
II(J-A), can now be found:
II(J-A) = T R(max)/P(max)
The heatsink for the LP2952 and LP2953 is made using the
PC board copper. The heat is conducted from the die,
through the lead frame (inside the part), and out the pins
which are soldered to the PC board. The pins used for heat
conduction are:
TABLE I
Pacl(age

Pins

LP2952N

14-PinDIP

3,4, 5, 10, 11, 12

LP2953N

16-PinDIP

4,5,12,13

LP2952M

16-Pin Surface Mt.

1,8,9,16

LP2953M

16-Pin Surface Mt.

1,8,9,16

~

CD

LP2952/
LP2953

Part

.....
r

"U

LO ---.-\.\

IIN- ....- - - - .
YIN ....;;;...-.... IN
OUT I--..;;.;~.,

P'-OTAL = (VIN - VOUT) IL

U1

Package

L(in.)

H(in.)

°J-ArC/W)

16-Pin DIP

1

0.5

70

2

1

60

3

1.5

58

4

0.19

66

6

0.19

66
65

14-Pin DIP

Surface Mount

1

0.5

2

1

51

3

1.5

49

1

0.5

83
70

2

1

3

1.5

67

6

0.19

69

4

0.19

71

0.19

73

2

2-115

Application Hints (Continued)
EXTERNAL CAPACITORS
A 2.2 /LF (or greater) capacitor is required between the output pin and ground to assure stability. Without this capacitor,
the part may oscillate. Most type of tantalum or aluminum
electrolytics will work here. Film types will work, but are
more expensive. Many aluminum electrolytics contain electrolytes which freeze at - 30"C, which requires the use of
solid tantalums below -2S·C. The Important parameters of
the capacitor are an ESR of about SO or less and a resonant frequency above SOD kHz (the ESR may increase by a
factor of 20 or 30 as the temperature Is reduced from 2S·C
to -30·C). The value of this capacitor may be Increased
without limit.
At lower values of output current, less output capacitance Is
required for stability. The capacitor can be reduced to
0.68 /LF for currents below 10 mA or 0.22 /LF for currents
below 1 mAo
Programming the output for voltages below SV runs the error amplifier at lower gains requiring more output capacitance for stability. For the worst-case condition of 1.23V
output and 250 mA of load current, a 6.8 /LF (or larger)
capacitor should be used.
A 1 /LF capacitor should be placed from the Input pin to
ground if there Is more than 10 Inches of wire between the
Input and the AC filter capacitor or If a battery Input Is used.
Stray capacitance to the Feedback terminal can cause Instability. This problem Is most likely to appear when using
high value external resistors to set the output voltage. AddIng a 100 pF capacitor between the Output and Feedback
pins and Increasing the output capacitance to 6.8 /LF (or
greater) will cure the problem.

Sii'ii'fDO\VN
INPUT"
OFF.-r ON

TL/H/11127-9

FIGURE 3. Adjustable Regulator

·s•• Application Hints
"D~v.

with TTL·low to shut down

DROPOUT VOLTAGE
The dropout voltage of the regulator Is defined as the minimum Input-to-output voltage differential required for the output voltage to stay within 100 mV of the output voltage measured with a 1V differential. The dropout voltage Is Independent of the programmed output voltage.
DROPOUT DETECTION COMPARATOR
This comparator produces a logic "LOW" whenever the output falls out of regulation by more than about S%. This figure results from the comparator's built-In offset of 60 mV
divided by the 1.23V reference (refer to block diagrams on
page 1). The S% low trip level remains constant regardless
of the programmed output voltage. An out-of-regulation condition can result from low input voltage, current limiting, or
therrnallimiting.
Figure 4 gives a timing diagram showing the relationship
between the output voltage, the 'EFi'FiOR output, and input
voltage as the Input voltage is ramped up and down to a
regulator programmed for SV output. The ERROR signal becomes low at about 1.3V Input. It goes high at about SV
input, where the output equals 4.75V. Since the dropout
voltage is load dependent, the Input voltage trip points will
vary with load current. The output voltage trip point does
not vary.
The comparator has an open-collector output which requires an external pull-up resistor. This resistor may be connected to the regulator output or some other supply voltage.
USing the regulator output prevents an invalid "HIGH" on
the comparator output which occurs if it is pulled up to an
external voltage while the regulator input voltage is reduced
below 1.3V. In selecting a value for the pull-up resistor, note
that while the output can sink 400 /LA, this current adds to
battery drain. Suggested values range from 100 kO to
1 MO. This resistor is not required if the output is unused.
When VIN S; 1.3V, the error flag pin becomes a high impedance, allowing the error flag voltage to rise to its pull-up
voltage. Using VOUT as the pull-up voltage (rather than an
external 5V source) will keep the error flag voltage below
1.2V (typical) in this condition. The user may wish to divide
down the error flag voltage using equal-value resistors
(10 kO suggested) to ensure a low-level logiC signal during
any fault condition, while still allowing a valid high logic level
during normal operation.

PROGRAMMING THE OUTPUT VOLTAGE
The regulator may be pin-strapped for SV operation using its
internal resistive divider by tying the Output and Sense pins
together and also tying the Feedback and 5V Tap pins together.
Alternatively, it may be programmed for any voltage between the 1.23V reference and the 30V maximum rating
using an external pair of resistors (see Figure 3). The complete equation for the output voltage is:

+ :~) + (IFB X

VOUT

1.2-30V

. -......+-1

MINIMUM LOAD
When setting the output voltage using an external resistive
divider, a minimum current of 1 /LA Is recommended through
the resistors to provide a minimum load.
It should be noted that a minimum load current is specified
in several of the electrical characteristic test conditions, so
this value must be used to obtain correlation on these tested limits.

VOUT = VREF X (1

-ERROR
OUTPUT

R1)

where VREF is the 1.23V reference and IFB is the Feedback
pin bias current (-20 nA typical). The minimum recommended load current of 1 /LA sets an upper limit of 1.2 MO
on the value of R2 in cases where the regulator must work
with no load (see MINIMUM LOAD). IFB will produce a typical 2% error in VOUT which can be eliminated at room temperature by trimming R1. For better accuracy, choosing
R2 = 100 kO will reduce this error to 0.17% while increasing the resistor program current to 12 /LA. Since the typical
quiescent current is 120 /LA, this added current is negligible.

2-116

r

reduces power dissipation, which results in die cooling. This
allows the part to turn back ON, and the cycle starts over.
If the part is operated above 125·C, the shutdown pin must
be connected to the regulator input voltage through a pullup resistor to assure that the regulator remains ON. This
resistor is not required for operation between -40·C and
+ 125·C, but can be used without affecting performance.

Application Hints (Continued)

ERROR
OUTPUT

------

~
.75V--

OUTPUT
VOLTAGE

---.

I
I
I

I
I
I

I

I

I

I

*:

:.-_.,.

Pinout Drawings

."

~

U'I

~
r

."
N
CD
U'I

~r

."

~

LP2952
14-Pln DIP

U'I

LP2952
16-PlnSO

Co)
......

r

."

INPUT
VOLTAGE

FIGURE 4. ERROR Output Timing

IS

GROUND

OUTPUT

Ne

15

~PUT

GROUND

OUTPUT

I.

FEEDBACK

GROUND

II

GROUND

SENSE

13

5V TAP

GROUND

10

GROUND

SHUTDOWN

3

REFERENCE

INPUT

5VTAP

"Exact value depends on dropout voltage. (See Application Hints)

I

12

GROUND

'In shutdown mode. ERROR will go high if it has been pulled up to an
external supply. To avoid this invalid response. pull up to regulator autpul.

GROUND

13

ERROR

TL/H/11127-10

S£HSE

I.

SHUTDOWH

ERROR

FEEIl8ACK

NO
GROUND

TL/H/11127-11

•
"
•
5

7

12

REFERENCE

II

Ne
Ne

10

•

GROUND

TLlH/11127-12

OUTPUT ISOLATION
The regulator output can be left connected to an active voltage source (such as a battery) with the regulator input power shut off. as long as the regulator ground pin Is connected to ground. If the ground pin is left floating. damage
to the regulator can occur if the output is pulled up by an
external voltage source.

LP2953
16-Pin DIP
5V TAP
INPUT
GROUND

REDUCING OUTPUT NOISE
In reference applications it may be advantageous to reduce
the AC noise present on the output. One method is to reduce regulator bandwidth by increasing output capacitance.
This is relatively inefficient. since large increases in capacitance are required to get significant improvement.
Noise can be reduced more effectively by a bypass capacitor placed across R1 (refer to Figure 3). The formula for
selecting the capacitor to be used is:

C _

I

FEEDBACK

GROUND

•

OUTPUT

Ne

7

SENSE

8

LP2953
16-PinSO

I"
15

REFERENCE

I.

COWP

13

I

Ne

2

I"
15

OUlPUT

3

I.

SENSE

4

SHUTDOWN

5

12

5V TAP
REFERENCE

"

II

COMP INPUT

10

COMP OUT
GROUND

our

12

GROUND
GROUND

II

Ne

10

ERROR
SHUTDOWN

•

GROUND

COMP INPUT

[ORO'

Ne
GROUND

7

8

TLlH/11127-13

13

•

GROUND
INPUT
fEEO!lACJ(

TL/H/11127-14

1

B - 21T R1 X 20 Hz

This gives a value of about 0.1 ",F. When this is used, the
output capacitor must be 6.8 ",F (or greater) to maintain
stability. The 0.1 ",F capacitor reduces the high frequency
gain of the circuit to unity, lowering the output noise from
260 ",V to 80 ",V using a 10 Hz to 100 kHz bandwidth. Also,
noise is no longer proportional to the output voltage, so improvements are more pronounced at high output voltages.

Ordering Information

AUXILIARY COMPARATOR (LP2953 only)
The LP2953 contains an auxiliary comparator whose inverting input is connected to the 1.23V reference. The auxiliary
comparator has an open-collector output whose electrical
characteristics are similar to the dropout detection comparator. The non-inverting input and output are brought out for
external connections.

LP2952AIN

LP2952
Order Number
LP29521N

LP29521M

Temp. Range
(TJ) ·C

Package

NSCDrawlng
Number

-40 to +125

14-Pin
Molded DIP

N14A

-40to +125

l6-Pin
SurfaceMt.

M16A

Temp. Range
(TJ) ·C

Package

NSCDrawing
Number

+ 125

l6-Pin
Molded DIP

N16A

-40 to + 125

16-Pin
SurfaceMt.

M16A

LP2952AIM
LP2953
Order Number

SHUTDOWN INPUT
When the operating junction temperature is between -40·C
and + 125·C, the shutdown input may be left open (floating)
for normal regulator operation (regulator output ON).
Operation at junction temperatures above the 125·C maximum (which is not recommended) has shown that leaving the shutdown pin open may cause the part to turn ON
and OFF. This occurs when internal leakage current activates the shutdown pin, causing the output to go OFF. This

LP29531N

-40 to

LP2953AIN
LP29531M
LP2953AIM

2-117

N

CD
U'I

;

Typical Applications

Basic 5V Regulator

5V Current Limiter with Load Fault Indicator
SV BUS

+VIN

SV TAP VOUT 1-_...._.-.
FB

1}1oF

SENSE

SV OUT
OUTPUT

t-t-......-t--lH~ .4.3-SV

LP2952/
LP29S3

10k

"R1
GND

t--+-t-4H~ FAULT

S.1k
TL/H/11127-15

TLlH/11127-16

'Output voltage equals + VIN minum dropout voltage, which varies with out·
put current. Current limits at a maximum of 3BO mA (typical).
"Select Rl so that the comparator input voltage is 1.23V at the output
voltage which corresponds to the desired fault current value.

Low T.C. Current Sink
V+ = 2.3 to 30V

5V Regulator with Error Flags for
LOW BATTERY and OUT OF REGULATION

.__ lt~
I

1::=:::

:

LOAD

I

:'I,=1.23
I

I

+

I

R

+VIN
6Y

374k

[

==

I pF

5Y TAP Your
FB
SENSE

LP29S3
COMP
INPUT

COMP
OUT

INPUT
,-ON

so

5Y OUT
1M :

1M

• LOW BATT

ERR

VOUT

SiWfiiOWN

-

lOOk

LP2952/
LP2953

GND

1 II117.2.2

• OUT OF
REGULATION

..L

GND

FB
TLlH/11127-1B

OFF --J

'Connect to Logic or I'P control inputs.
LOW BATT flag wams the user that the battery has discharged down to
aboutS.BV, giving the user time to rachargethe battery or power down some
hardware with high power requirements. The output Is stili in regulation at
this time.
OUT OF REGULATION flag Indicates when the battery is almost completely
discharged, and can be used to InUiate a power·down sequence.

+ 10}loF
R

TLlH/11127-17

2·118

Typical Applications (Continued)

5V Battery Powered Supply with Backup and Low Battery Flag
5V OUT
(MAl N)

RECHARGE
CIRCUITRY

cp

~1~F

PWR
ON

..... 1
..... t
IN
914

The circuit switches to the

NI·CAD backup battery
when the main battery Yoll·
age drops below about
5.6V. and returns to Ihe
main battery when its Yoll·
age is recharged to about
6V.
The 5V MAIN outpuI pow·
ers circuitry which requires
no backup. and the 5V
MEMORY output powers
critical circuitry whi ch can
not be allowed to losepower.
'The BATTERY LOW flag
goes low whenever the cir·
cuit switches to the NI·CAD
backup battery.

-

6V +-_LEAD :E:
ACID
IN -:
MAIN
914 ....

=-=

""'""

.

lOOk
1"

510k

.

3.65
MEG
1"

1 ~r

FB

SENSE
LP2953

COMP
INPUT
ERR
~~

0.1

T~r

FB

]

lOOk

~F

LP2953

GND

i

2.2

VPI2A
51k

COMP
OUT

1::
I-..:.

I
-

150k

-b

.~

""""5V

__L...+

NICAD
BACKUP

:E:

t

VINO~

+VIH
5V TAP VOUT

==

COMP
INPUT

Timing Diagram for Timed Power-On Reset

I
I

[

SNS
5V TAP

TL/H/11127-19

VIN

RT

I

5V OUT
(ME MORY)

'BATT LOW
FLAG

5V Regulator with Timed Power-On Reset

1 MEG

.....
....

Your

+VIN

SO
1 ~F

,

lA SCHOTTKY

/383k
1"

COMP
OUT

GND

5V OUT

VOUT

---:;:"

==
",r
2.2

~

.8V_o_

o

~
I

I

lOOk
RESET

:

5V

r

-+/ 28 mo' I-- nME DELAY

RESET
TO ",p

TL/H/11127-21

'RT

1

..L
TLlH/11127-20

2-119

~

1 MEG.

Or

~

0.1 I'F

Typical Applications (Continued)

5V Regulator with Snap-On/Snap-Off
Feature and Hysteresis

5V Regulator with Error Flags for
LOW BATTERY and OUT OF REGULATION
with SNAP-ON/SNAP-oFF Output

~.-~------.----------------,
374k
1%

+VIH

pF
2~~

--t--+-••

SV TAP Vour t - -.......
FB
SENSE
1 }.IF

10
M

r-"

187k

SV OUT

LP2952

220

SHUT
OOWN

+V'N
5V TAP VOUT
FB

II'F

I-_+-..._ ......_ -+
PF

2k

._=,-6V

;:

SENSE
LP2953

CaMP
INPUT
49.9k

5V OUT

-

1M

CaMP
OUT

S7D

lOOk
1%

GNO

[

• LOW BATT

ERR
• OUT OF
REGULATION

GND

I
..L

TLlH/11127-22

1M

I~

1'2.2

'Turns ON at Y,N ~ 5.B7V

TLlH/11127-23

Turns OFF at Y'N ~ 5.64V

'Connect to Logic or ",p control inputs.

(for component values shown)

OUTPUT has SNAp·ON/SNAp·OFF feature.
LOW BAIT flag warns the user that the battery has discharged down to
about 5.BV, giving the user time to recharge the battery or shut down hard·
ware with high power requirements. The output is still in regulation at this

time.
OUT OF REGULATION flag goes low if the output goes below about 4.7V,
which could occur from a load fault.
OUTPUT has SNAP·ON/SNAP·OFF feature. Regulator snaps ON at about

5.7V Inpu~ and OFF at about 5.SV.

5V Regulator with Timed Power-On Reset, Snap-on/Snap-Off Feature and Hysteresis
Timing Diagram

VIN

]~o
~F

374k
1%

7.SM

[
.=;:
1

R
1M

}.IF

....... I-lOOk
1%

V

+VIN

~.",C
TO.l}.1F

SV TAP Your
FB
SENSE
LP2953
CaMP
INPUT COMP
OUT

-

S7D

1

'

• _. S.64V
~
I
I

S.87L _ .

IN

I

I

VOUTO~

1M

RESET
TO }.IP

ERR GNO

..L

SV OUT

I

RESET

--:

F L
TO

TL/H/11127-25

I~

Td

1'2.2
}.IF
TLlH/11127-24

2-120

~

(0.2B) RC

~

2B ms for components shown.

,------------------------------------------------------------------------, "a
~
~

~National

CD

UI

~ Semiconductor

~

!;;
~

CD

LP2954/LP2954A
5V Micropower Low-Dropout Voltage Regulators
General Description

Features

The LP2954 is a three-terminal, 5V micropower voltage regulator with very low quiescent current (90 p.A typical at 1 mA
load) and very low dropout voltage (typically 60 mV at light
loads and 470 mV at 250 mA load current).

•
•
•
•
•
•
•
•
•

The quiescent current increases only slightly at dropout
(120 p.A typical), which prolongs battery life.
The LP2954 is available in the three-lead TO-220 package,
which makes heatsinking very simple.
Reverse battery protection is provided.
The tight line and load regulation (0.04% typical), as well as
very low output temperature coefficient make the LP2954
well suited for use as a low-power voltage reference.
The accuracy of the 5V output is guaranteed at both room
temperature and over the entire operating temperature
range.

UI

:t

5V output within 1.2% over temperature (A grade)
Guaranteed 250 mA output current
Extremely low quiescent current
Low dropout voltage
Reverse battery protection
Extremely tight line and load regulation
Very low temperature coefficient
Current and thermal limiting
Pin compatible with LM2940 and LMS40

Applications
• High-efficiency linear regulator
• Low dropout battery-powered regulator

Package Outline and Ordering Information

Typical Application Circuit

Ordering Information
Order Number
LP2954AIT

Temp. Range
(TJ) 'C
-40 to +125

Package NSPackage
(JEDEC)
Number
TO-220

TOSe

LP29541T

OUT

IN

VIN

' 't

LP2954
GND

-b
-

TO·220 3·Lead Plastic Package

TL/H/11128-2

Front View

2·121

5V OUT

T"" ~
-

TL/H/11128-1

II

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Operating Junction Temperature Range
LP2954AIILP29541
-40"Cto +125'C
Storage Temperature Range
- 65'C to + 150'C

Lead Temperature
(Soldering, 5 seconds)
Power Dissipation (Note 2)

260"C
Internally Limited
-20Vto +30V

Input Supply Voltage
ESDRating

Electrical Characteristics Limits in standard typeface are for TJ =

2kV

25'C, bold typeface applies over the

- 40'C to + 125'C temperature range. Limits are guaranteed by production testing or correlation techniques using
standard Statistical Quality Control (SQC) methods. Unless otherwise noted: VIN = 6V, IL = 1 mA, CL = 2.2 /LF.
Symbol

Parameter

Conditions

2954AI

Typical
Min

Va

Output Voltage

5.0
1 mA :s; IL :s; 250 mA

AVO
AT

Output Voltage
Temp. Coefficient

(Note 3)

AVO

Line Regulation

VIN = 6V to 30V

5.0

20
0.03

Va
AVO

Load Regulation

Va
VIN-VO

Dropout Voltage
(Note 5)

IL = 1 to 250 mA
IL = 0.1 to 1 mA
(Note 4)
IL= 1 mA
IL = 50mA
IL = 100mA
IL = 250mA

IGND

Ground Pin Current
(Note 6)

IL = 1 mA
IL = 50mA
IL = 100mA
IL = 250 mA

IGND

ILiMIT

Ground Pin
Current at Dropout
(Note 6)

VIN = 4.5V

Current Limit

VOUT = OV

0.04

60
240
310
470
90
1.1
4.5
21

120

AVO
APd

Thermal Regulation

(Note 7)

en

Output Noise
Voltage
(10 Hz to 100 kHz)
IL = 100mA

CL = 2.2 /LF

380
0.05

29541
Max

Min

Units
Max

4.975

5.025

4.950

5.050

4.940

5.060

4.900

5.100

4.930

5.070

4.880

5.120

100

150

0.10

0.20

0.20

0.40

0.16

0.20

0.20

0.30

100

100

150

150

300

300

420

420

400

400

520

520

600

600

800

800

150

150

180

180

2

2

2.5

2.5

6

6

8

8

28

28

33

33

170

170

210

210

500

500

530

530

0.2

0.2

V

ppml'C
%

%

mV

/LA

mA

/LA

mA

%/W

400
/LVRMS

CL = 33/LF

260

2·122

Electrical Characteristics (Continued)
Note 1: Absolute maximum ratings indicate limits beyond which damage to the component may occur. Electrical specifications do not apply when operating the
device outside of its rated operating conditions.
Note 2: The maximum allowable power dissipation is a function of the maximum junction temperature, TJ (MAX), the junction-to-ambient thermal resistance, 9J-A'
and the ambient temperature, TA. The maximum allowable power dissipation at any ambient temperature is calculated using: P(MAX)

~

TJ (M:X) - TA.
J·A

Exceeding the maximum allowable power dissipation will result in excessive die temperature, and the regulator will go into thermal shutdown. The junction·to-ambi-

ent thenmal resistance of the LP2954 (without extemal heatsink) is 60" C/W. The junction-to-case thenmal resistance is 3 ·CIW. If an extemal heatsink is used, the
effective junction-to-ambient thermal resistance is the sum of the junction-to-case resistance (3 GC/W), the specified thermal resistance of the heatsink selected,
and the thermal resistance of the interface between the heatsink and the LP2954. Some typical values are listed for interface materials used with T0-220
packages:

Typical Values of Case-to-Heatsink Thermal Resistance rC/W)
TABLE I. (Data from AAVID Eng.)

TABLE II. (Data from Thermalloy)

Silicone grease

1.0

Thermasillll

1.3

Dry interface

1.3

Thermasilll

1.5

Mica with grease

1.4

Thermalfilm (0.002)
with grease

2.2

Note 3: Output voltage temperature coefficient is defined as the worst case voltage change divided by the total temperature range.
Note 4: Regulation is measured at constant junction temperature using low duty cycle pulse testing. Parts are tested separately for load regulation in the load
ranges 0.1-1 rnA and 1-250 rnA. Changes in output voltage due to heating effects are covered by the thenmal regulation specification.
Note 5: Dropout voltage Is defined as the input to output differential at which the output voltage drops 100 mV below the value measured with a 1V differential.
Note 6: Ground pin current is the regulator quiescent current. The total current drawn from the source is the sum of the load current plus the ground pin current.

Note 7: Thermal regulation is defined as the change in output voltage at a time T after a change in power dissipation is applied, excluding load or line regulation
effects. Specifications are for 200 mA load pulse at VIN ~ 20V (3W pulse) for T ~ 10 ms.
Note 8: When used in dual-supply systems where the regulator load is returned to a negative supply, the output voltage must be diode-clamped to ground.

2·123

Typical Performance Characteristics
Quiescent Current
'20
1
'§' 100

80

§!

40

!

"-

0

-:c

..3

iB

l"'00pA

~ eo
~

100

I
J

20

100

r-...

90

!

A

INPUT VOLTAGE (V)

~

20
18
18

"\l.

r-

1

la2'0~A

10
8

1

15

~

10

0

'"~

!

z

i;

l5

~

iil

~

D!

l- I-

--

~

80

l al

\
\\

50
40
30

.:!!.

VIH~~~I
'1.=2
• •F

20
0.01

0.1

1

All

l5

/I
I

iil

,r ~
VI.. 'OmA

"
10

100

~

~

D!

70
60

100Ripple

~ L fOO A
II

i;

.:!!.

............ ~\

!iil

,\

~·25DmA

\\

~

0.1

I

'\

VIN~~~~pF
'1.=2.

10
0.01

10

"-V

1

10

100

"'~'>
~E

o~

V

>"'

~~

1000

J
1000

~

D!

Rejection

1\

80

,..

70
laO

60

V£

f\ V V
\V ~'OOPA

50
'0

VINllt~~.
11.
::112. pF

30

20
0.01

0.1

V
10

100

1000

100

1000

FREQUENCY (kHz)

Line Transient Response
!1.~!.E-

8D

100

LOAD CURRENT (mA)

FREQUENCY (kHz)

'1. "2.~"F
l='O A

V

:--.....

3D

Line Transient Response

1\

0.1

90

50

FREQUENCY (kHz)

100
0

'0

20

1000

~

F

l"I'00ImA

Ripple Rejection

i;

1

300
200

90

1\

~

tl

80

./

1000

IN

1
-22

'00

Ict.L

g

JUNCTION TEMPERATURE (OC)

11

,:;
..3

~

INPUT VOLTAGE (V)

70

....E
~

-75-50-25 0 25 50 75 100125150

80

100

500

;:!

o

Ripple Rejection

10

Output Noise Voltage

0123'5878

90

1

OUTPUT CURRENT (mA)

z

o

.:!!.

20

i8

0

100

0.1

Ground Pin Current
25

1

"12

i

TEMPERATURE (OC)

Ground Pin Current

I

ln-"

80

0:
o

70
-75 -50-25 0 25 50 75 100125150

0123'5878

-:c

z

...... r--.

~

!

10

I

I"

~

o

.s

Ground Pin Current vs Load

Quiescent Current
110

140

Output Impedance
100

\.=~1--

'0

10

II

SO
0
-40

... "'
~

8V

>

6V

~;

"'
~~

i!5o
>

0.1

8V
8V

0.01
0.2

D.'

0.6

TIME (ms)

0.01

0.8
TIME (m.)

0.1

10
FREQUENCY (kHz)

TL/H/11128-3

2-124

Typical Performance Characteristics
Load Transient Response
800

Load Transient Response

'IN=IV

200

w

f!s:s..5

~=. p

~~
S~

0

~t=1=ttt++t:t~

u

100pA

20

l =25QmA

~ ;250mA

0",

1

~:>

1-+--1-+-+-+-++++-1
10

l"100~A

-100

-200

~ ~250mA1'-+++++-+-+-+-!--I

9:5

Dropout Characteristics

YIH s6V

100

>w

-800

(Continued)

u 100pA

30

10

TIWE(ms)

20

30

40

50

o

o

60

600

~~
o~

>w

~~

15
10
5

SD
0

-5

550

V

I....-

......

~

115

-4S0

~

400

500

:g

.... 350

ffi~

300

~

~~

~I

250
10

20

3

4

Short-Circuit Output
Current and Maximum
Output Current

Thermal Response
w

2

INPUT VOLTAGE (V)

TIWE(ms)

I

r-.......

uk DUb lRl,
l
N.

t"f- f-

~:"!.c ,","'
~i

CURRENT

r.-:

I
I

200
-75-50-25 0 25 50 75 100125150

30

TIWE(ms)

JUNCTION TEMPERATURE (DC)

TL/H/11128-4

fII

2-125

Application Hints
EXTERNAL CAPACITORS
A 2.2 p.F (or greater) capacitor is required between the
output pin and the ground to assure stability (refer to Figure
1). Without this capacitor, the part may oscillate. Most types
of tantalum or aluminum electrolytics will work here. Film
types will work, but are more expensive. Many aluminum
electrolytics contain electrolytes which freeze at - 30"C,
which requires the use of solid tantalums below - 2SoC. The
important parameters of the capacitor are an ESR of about
sa or less and a resonant frequency above SOO kHz (the
ESR may increase by a factor of 20 or 30 as the temperature is reduced from 2SoC to -30"C). The value of this capaCitor may be increased without limit. At lower values of
output current, less output capacitance is required for stability. The capacitor can be reduced to 0.68 p.F for currents
below 10 mA or 0.22 p.F for currents below 1 mA.

TL/H/II12S-5

'See External CapaCitors
Protal

= (YIN

-5) IL + (YIN) IG

FIGURE 1. Basic 5V Regulator Circuit
the circuit. The formula for calculating the power dissipated
in the regulator is also shown in Figure 1.

A 1 p.F capacitor should be placed from the input pin to
ground if there is more than 10 inches of wire between the
input and the AC filter capacitor or if a battery input is used.

The next parameter which must be calculated is the maximum allowable temperature rise, T R(max). This is calculated by using the formula:

MINIMUM LOAD

TR(max) = TJ(max) - TA(max)

It should be noted that a minimum load current is specified
in several of the electrical characteristic test conditions, so
this value must be used to obtain correlation on these tested limits. The part is parametrically tested down to 100 p.A,
but is functional with no load.

where: TJ(max) is the maximum allowable junction
temperature
T A(max) is the maximum ambient temperature
Using the calculated values for T R(max) and P(max), the
required value for junction-to-ambient thermal resistance,
8(J-A), can now be found:

DROPOUT VOLTAGE
The dropout voltage of the regulator is defined as the minimum input-to-output voltage differential required for the output voltage to stay within 100 mV of the output voltage measured with a 1V differential. The dropout voltages for various
values of load current are listed under Electrical Characteristics.

8(J-A) = T R(max)/P(max)
If the calculated value is 60° C/W or higher, the regulator
may be operated without an external heatsink. If the calculated value is below 60" C/W, an external heatsink is required. The required thermal resistance for this heatsink can
be calculated using the formula:

If the regulator is powered from a rectified AC source with a
capacitive filter, the minimum AC line voltage and maximum
load current must be used to calculate the minimum voltage
at the input of the regulator. The minimum input voltage,
Including AC ripple on the filter capacitor, must not drop
below the voltage required to keep the LP29S4 in regulation.
It is also advisable to verify operating at minimum operating
ambient temperature, since the increasing ESR of the filter
capacitor makes this a worst-case test for dropout voltage
due to increased ripple amplitude.

8(H-A) = 8(J-A) - 8(J-C) - 8(C-H)
where:
8(J-C) is the junction-to-case thermal resistance, which is
specified as 3° C/W maximum for the LP29S4.
8(C-H) is the case-to-heatsink thermal resistance, which is
dependent on the interfacing material (if used). For details
and typical values, refer to Note 2 listed at the end of the
ELECTRICAL CHARACTERISTICS section.
8(H-A) is the heatsink-to-ambient thermal resistance. It is
this specification (listed on the heatsink manufacturers data
sheet) which defines the effectiveness of the heatsink. The
heatsink selected must have a thermal resistance which is
equal to or lower than the value of 8(H-A) calculated from
the above listed formula.

HEATSINK REQUIREMENTS
A heatsink may be required with the LP29S4 depending on
the maximum power dissipation and maximum ambient temperature of the application. Under all possible operating
conditions, the junction temperature must be within the
range specified under Absolute Maximum Ratings.

OUTPUT ISOLATION

To determine if a heatsink is required, the maximum power
diSSipated by the regulator, P(max), must be calculated. It is
important to remember that if the regulator is powered from
a transformer connected to the AC line, the maximum
specified AC Input voltage must be used (since this produces the maximum DC input voltage to the regulator). Figure 1 shows the voltages and currents which are present in

The regulator output can be left connected to an active voltage source (such as a battery) with the regulator input power turned off, as long a8 the regulator ground pin Is connected to ground. If the ground pin is left floating, damage
to the regulator can occur if the output is pulled up by an
external voltage source.

2-126

Typical Applications

5V Regulator

5V Current Limiter
5V BUS

--+ VOUT

t -....

lpF

---+-+

VOUTt-....

LP2954

OUTPUT
• •• 3V - 5V

TL/H/II12B-6

GND

1 pF

TLlH/II12B-7

'Oulput voltage equals + VIN minus dropout voltage, which varies with output current. Current limits at 380 mA (typical).

Schematic Diagram

IN

•
TL/H/II12B-B

2-127

Section 3
Switching Voltage
Regulators

&I

Section 3 Contents
Switching Voltage Regulators Definition of Terms. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . • . . . . .
SWitching Voltage Regulators Selection Guide....... ........ ...................... ....
HS7067 7-Amp, Multimode, High Efficiency Switching Regulator. .... ...... ............•..
LH1605/LH1605C 5 Amp, High Efficiency Switching Regulators. ..... ...•...•..........•.
LM1524D/LM2524D/LM3524D Regulating Pulse Width Modulators................ ......
LM2574/LM2574HV Series Simple Switcher 0.5A Step-Down Voltage Regulators ..........
LM1575/LM1575HV/LM2575/LM2575HV Simple Switcher 1A Step-Down Voltage
Regulators ......................................................................
LM2576/LM2576HV Simple Switcher 3A Step-Down Voltage Regulators. . . . . . .. . . . . . . . . ..
LM1577/LM2577 Simple Switcher Step-Up Voltage Regulators ..................•.......
LM1578A1LM2578A1LM3578A Switching Regulators. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ..
LM78S40 Universal Switching Regulator Subsystem .......... . . . . . . . . . . . . . . . . . . . . . . . . ..
LMC7660 Switched Capacitor Voltage Converter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ..

3·2

3-3
3-5
3-7
3-16
3-19
3-36
3-54
3-71
3-87
3-109
3-123
3-130

~National

~ Semiconductor

Switching Regulators
Definition of Terms
Boost Regulator: A switching regulator topology in which a
lower DC voltage is converted to a higher DC voltage. Also
known as a Step-Up Regulator.

Diode Recovery Time: The period of time it takes the current through a diode to return to zero after the forward voltage is removed (i.e., the diode is turned OFF).

Buck Regulator: A switching regulator topology in which a
higher DC voltage is converted to a lower DC voltage. Also
known as a Step-Down Regulator.

Discontinuous Mode Operation: See Continuous Mode
Operation.
Efficiency ('1): The proportion of input power actually delivered to the load.

Buck-Boost Regulator: A switching regulator topology in
which a positive DC voltage is converted to a negative DC
voltage without the use of a transformer. A variation of this
topology produces a positive DC output voltage which is
between the positive DC input voltage maximum and minimum limits, i.e., providing both buck and boost functions.

n = POUT =
PIN

POUT
POUT + PLOSS

Electromagnetic Interference (EM I): A generic term which
is used to refer to any type of unwanted electromagnetic
radiation coming from a system such as a switching regulator.
Emitter Saturation Voltage: With the collector pulled up to
the DC input voltage and the switch ON, the collector-toemitter voltage of a NPN transistor switch at a specified
emitter current.
Error Amplifier (or Comparator): An amplifier (or comparator) which is used to detect the difference between a feedback voltage (usually proportional to the output voltage) and
a DC reference voltage. The resulting error voltage is used
in the regulator control circuitry to adjust the switch on-time.
This error amplifier may be either a transconductance-type
or an operational amplifier.
ESR: A parasitic element of every capaCitor, the ESR
(equivalent series resistance) is the purely resistive component of a real capaCitor's impedance. It is modeled as a
resistor in series with the capacitive element, and its value is
usually determined by the device construction.

Burst Mode: The mode of operation in a switching regulator
that results when the load current is reduced to the point
where the minimum duty cycle of each pulse provides more
energy than the load demands, thus causing the controller
to "skip" pulses (or sets of pulses) to maintain the output
voltage at its correct value.
Duty Cycle (D): The ratio of the period of time the output
switch is ON to the total oscillator period.

D = tON/T
CapaCitor Ripple Current: The RMS value of the maximum
allowable alternating current at which a capaCitor can be
operated continuously at a specified temperature. This parameter is specified by the capacitor manufacturer, and
must be considered when a capacitor is used as part of a
switching regulator input or output filter.
Catch Diode: The diode which provides a return path for
the load current when the regulator switch is OFF. For
switching regulators, the types of diodes normally used include Schottky-barrier, fast-recovery, and ultra-fast recovery. Also known as a steering diode or free-wheeling diode.

ESL: A parasitic element of every capaCitor, which limits its
effectiveness at high frequencies. The ESL (equivalent series inductance) is the pure inductance component of a device. Its value is usually determined by the device construction, espeCially its leads. It is modeled as an inductor in
series with the capacitive element.
EeTop: See Operating Volt-Microsecond Constant.

Collector Saturation Voltage: With the emitter grounded
and the switch ON, the collector-to-emitter voltage of an
NPN transistor switch at a specified collector current.
Compensation: The circuitry required to provide adequate
stability for the regulator control loop.

Flyback Regulator: A switching regulator topology in which
a DC voltage is converted to another DC voltage by means
of a transformer which stores energy delivered by a switch
during the switch ON time, and transfers the energy to an
output storage capaCitor during the switch OFF time.

Continuous Mode Operation: Relates to the inductor current. In the continuous mode, the inductor current is always
greater than zero. In discontinuous mode, the inductor current falls to zero before the end of each switching cycle.
Current Umlt Sense Voltage: For regulator ICs that have
externally-controlled current limit, the current limit sense
voltage is the voltage that must be applied (between two
specified pins) to turn the output transistor OFF and start
other current limit functions within the IC.

Inductor Ripple Current (aIIND): The peak-to-peak value
of the inductor current waveform, typically a sawtooth waveform when the regulator is operating in the continuous
mode.
Inductor Saturation: The condition which exists when an
inductor cannot hold any more magnetic flux. When an inductor saturates, its inductance appears to decrease and
the resistive component dominates. Inductor current is then

Current-Mode Control: A method of feedback control used
in switching regulators where both the output voltage and
the switch current are used to control the switching element.

3-3

o ,---------------------------------------------------------------------------------,

E

{!!.

oc
o

:1:1
·c

~
f

i=
Q

CP

a::
Q

C

I

limited only by the DC resistance of the wire and the available source current.
Inverting Regulator: A switching regulator which converts
a positive DC voltage to a negative DC voltage. The buckboost topology is often used for this function.
MagnetiC Flux Interference: Unwanted interference emitted by magnetiC components (transformers and inductors)
in the form of magnetiC flux. Magnetic flux interference can
be minimized by the use of magnetic cores (such as toroid
or pot core) which contain the flux, or by shielding with materials such as steel or mu-metal. Aluminum and copper are
not effective in shielding flux.
Operating Volt-Microsecond Constant: The product (in
Volts x microseconds) of the voltage applied to the switching regulator inductor and the period of time the voltage Is
applied. Abbreviated as EeTop, this constant is a measure
of the energy-handling capability of an inductor, and is dependent upon the type of core used, its core area, the number of turns of wire used, and the applied duty cycle.
Oscillator Frequency: The frequency of the internal oscillator used in the control of the switching regulator. Generally
the same as the switching frequency, for most regulators
the oscillator frequency is fixed, either internally or by an
external resistor and/or capacitor.
Output Ripple Voltage: The AC component of the switching regulator output voltage. it is usually dominated by the
output capacitor ESR multiplied by the applied ripple current, but may have high-frequency spikes caused by effects
of output capacitor ESL.
Pulse·Wldth Modulation (PWM): A method of control used
in a Switching regulator where the duty cycle of the switchIng element Is used to control the output voltage.

Radio Frequency Interference (RFI): High-frequency electromagnetic radiation resulting from the high switching
speeds of switching transistors and rectifiers, often causing
problems in nearby Circuitry that is sensitive to the large
noise "spikes" that are often associated with it. RFI can be
easily shielded by a good electrical conductor such as copper or aluminum.
Snubber: A network used to limit the voltage developed
across a component. The network usually consists of a zener diode, or a diode in series with a parallel resistor and
capaCitor. In a switching regulator, the snubber is most often used to limit the switch voltage of a flyback regulator.
Soft Start: In a switching regulator, a soft start limits the
duty cycle of the regulator during startup. This in turn limits
the energy the regulator demands from its source while
building up the output voltage from its initial condition of OV.
Standby Quiescent Current: For a regulator with an ONI
OFF pin, this is the supply current (or ground pin current)
required by the regulator IC when in the standby (OFF)
mode.
Switch: In a switching regulator, a transistor or MOSFET
used to deliver energy, in pulses, into energy storage devices (such as inductors, transformers, or capaCitors) for use
bya load.
Switching Frequency: See Oscillator Frequency.
Step Response: The transient response of a regulator output after the load current is "stepped" from one value to
another. This test is often used for evaluating the loop stability of a regulator.
Transient Response Time: The period of time it takes the
output of a regulator to return to a steady-state value after a
change in line voltage or load current. See also Step Response.

Voltage Mode Control: A method of control used in a
switching regulator where feedback from the output voltage
is used to provide control of the switching element.

3-4

~National

Semiconductor

Switching Voltage Regulators Selection Guide
Switching Voltage Regulators
Switch
Current
(A)

7.0

5.0

1.5

0.75

0.2

Standard
Operating
Modes

Input
Voltage
(V)

Output
Voltage
(V)

Switching
Frequency
(kHz)

HS7067

Step-Down, Flyback,
Invert

10 to 60

Adjustable

25 to 200

- 55'C to

HS7067C

Step-Down, Flyback,
Invert

10 to 60

Adjustable

25 to 200

- 25'C to + 150'C

Device

Operating
Temperature
(TJ)

+ 150'C

Package
Availability""

Page
No.

K8

3-7

K8

3-7
3-16

LH1605

Step-Down

8to 35

3t030

6 to 100

-55'C to + 150'C

K8

LH1605C

Step-Down

8t035

3t030

6 to 100

-25'Cto +150'C

K8

3-16

LM78S40

Step-Up, Step-Down,
Invert

2.5 to 50

Adjustable

0.1 to 100

-55'Cto +150'C

J16

3-123

LM78S40

Step-Up, Step-Down,
Invert

2.5 to 50

Adjustable

0.1 to 100

- 40'C to + 125'C

N16

3-123

LM78S40C

Step-Up, Step-Down,
Invert

2.5 to 50

Adjustable

0.1 to 100

O'Cto + 125'C

J16, N16

3-123

LM1578A

Step-Up, Step-Down,
Flyback, Invert

2t040

Adjustable

0.001 to 100

-55'C to + 150'C

H8

3-109

LM2578A

Step-Up, Step-Down,
Flyback, Invert

2t040

Adjustable

0.001 to 100

-40'C to + 125'C

H8, M8, NB

3-109

LM357BA

Step-Up, Step-Down,
Flyback, Invert

2t040

Adjustable

0.001 to 100

HB,MB,N8

3-109

LM1524D*

Step-Up, Step-Down,
Flyback, Invert

5t040

Adjustable

1 to 550

- 55'C to + 150'C

J16

3-19

LM2524D*

Step-Up, Step-Down,
Flyback, Invert

5to 40

Adjustable

1 to 550

- 40'C to

N16

3-19

LM3524D*

Step-Up, Step-Down,
Flyback, Invert

5t040

Adjustable

1 to 350

M16, N16

3-19

O'C to

+ 125'C

+ 125'C

O'C to + 125'C

·The O.2A switch current specification is the maximum capability for each of the dual internal NPN transistor switches.
"Under Package Availability the letter identifies the type of package available and the number indicates the number of leads of the indicated package.
For example: T5 ~ 5·Lead TO-220, and M14 ~ 14·Lead Surface Mount.
H: Metal Can (TO·gg)

J: Ceramic

Oual~ln-Une

Package

K: Metal Can (TO·3)
M: Small Outline Molded Package (Surface Mount)
N: Molded Dual·ln-Line Package

3-5

DC/DC Voltage Converters
Output
Current
(A)
3.0

1.0

0.5

0.05

Device

Standard
Input
Operating Voltage
Modes
(V)

Output
Voltage
(V)

Switching
Efficiency
Frequency
(%)
(kHz)

Operating
Temperature
(TJ)

Package
Availability"

Page
No.

K4'"

3·87

LM1577'

Step-Up,
Flyback

3.5 to 40 12, 15, Adjustable

52

80

-55·Cto +150·C

LM2577'

Step·Up,
Flyback

3.5 to 40 12, 15, Adjustable

52

80

- 55·C to + 150·C M24, N16, T5

3·87

LM2576

Step·Down

4t040

3.3,5,12,15,
Adj. (1.23 to 37)

52

77 to 88

-40·C to + 125·C

T5

3·71

LM2576HV Step· Down

4t060

3.3,5,12,15,
Adj. (1.23 to 57)

52

77 to 88

-40·C to + 125·C

T5

3-71

LM1575

Step· Down

4t040

5,12,15,
Adj. (1.23 to 37)

52

77 to 88

- 55·C to + 150·C

K4'"

3-54

LM2575

Step· Down

4t040

3.3,5,12,15,
Adj. (1.23 to 37)

52

77 to 88

- 40·C to + 125·C M24, N16, T5

3·54

LM2575HV Step·Down

4t060

3.3,5,12,15,
Adj. (1.23 to 57)

52

77 to 88

-40·Cto + 125·C M24, N16, T5

3-54

LM2574

Step·Down

4t040

3.3,5,12,15,
Adj. (1.23 to 37)

52

77 to 88

-40·C to + 125·C

M14,N8

3·36

LM2574HV Step·Down

41060

3.3,5,12,15,
Adj. (1.23 to 57)

52

77 to 88

-40·C to + 125·C

M14,N8

3-36

-1.5to -10

10

90

-40·C to + 125·C

N8

3-130

LMC76601

Invert

1.5to 10

'For the LMI577 and LM2577 the 3.0A output current specification indicates the current rating of the internal NPN transistor switch.
"Under Package Availability the letter identifies the type of package available and the number Indicates the number 01 leads of the indicated package.
For example: T5 = 5·Lead TO-220, and M14 = 14-Lead Surface Mount
K: Metal Can (TO·3)
M: Small Outline Molded Package (Surface Mount)
N: Molded Dual·ln·Line Package
T: TO·220
...Available in indicated package only as a military specified device.

3-6

r------------------------------------------------------------------.%
~
~National
....
~ Semiconductor
0)

HS7067 7 Amp, Multimode, High Efficiency
Switching Regulator
General Description

Features

The HS7067 is a hybrid high efficiency switching regulator
with high output current capability. The device is housed in a
standard TO-3 package containing a temperature compensated voltage reference, a pulse-width modulator with programmable oscillator frequency, error amplifier, high current, high voltage output switch and steering diode. The
HS7067 operates in a step-down, inverting, as well as in a
transformer-coupled mode.

•
•
•
•
•

HS7067-10V to 60V input
7A continuous output current
Frequency adjustable to 200 kHz
High-efficiency (>75%)
Standard a-pin TO-3 package

Typical Applications
•
•
•
•

The HS7067 can supply up to 7A of continuous output current over a wide range of input and output voltages.

7A step-down regulator
Inverting regulator
Multiple-output regulator
Isolated regulator

Block and Connection Diagrams
INPUT0-:5+_ _ _ _ _ _ _....._ _ _......_~

r-.....,-t--f..;,B-o OUTPUT

STEfRJNG
DIODE
(ANODE)
CLOCK 0 - : + - - - - - -.....
TIMING 0-:4+---1.....
CAP

ERROR

t - - - -...---+:-O AMP INPUT
t - - - -.....---+;;.-o EKTERNAL
CAP (Y!!EF)

PWM CONTROL
1
AND COMPENSATION 0 - : + - - - - - - - - - - -....
TL/K/6746-1

Metal Can Package

Order Number
HS7067CK, HS70671< or HS7067K-MIL
See NS Package Number K08A

TL/K/6746-2

Top View
Case is ground

3-7

•

Absolute Maximum Ratings
TA. Operating Temperature Range
HS7067C
HS7067
TSTG. Storage Temperature Range
VR(VB-7).
Steering Diode Reverse Vollage

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
65V
Y,N. Input Voltage
8A
'OUT. Output Current
TJ. Operating Temperature
150'C
po. Internal Power Dissipation
25W

- 25·C to + 85·C
- 55·C to + 125·C
-65·Cto + 150'C
105V

IO(l7-B).
Steering Diode Forward Current

8A

Electrical Characteristics Tc = 25·C. Y,N = 20V (unless otherwise specified) (Note 8)
Symbol

V,N-VOUT Min V,NIVOUT Differential
Vs

VF

Conditions

Parameter

Switch Saturation Voltage

Steering Diode On Voltage

Min Typ Max Units

10V ~ Y,N ~ V'N(MAX)
lOUT = 2A (Note 6)

3.0

= 7.0A. Y,N = 10V
Ic = 2.0A. Y,N = 10V
10 = 7.0A
'0 = 2.0A

1.6

Ic

1.9

1.0
1.3

Supply Voltage Range (Note 7)

TMIN ~ TA ~ TMAX

IR

Steering Diode Reverse Current

VR

10

Quiescent Current (Note 3)

0% Duty Cycle (VS

V2

Reference Voltage on Pin 2

TMIN ~ TA ~ TMAX

2.3

2.5

VClKH

Clock Output High

IClK

1.2

1.6

VClKl

Clock Output Low

= -750 /LA
IClK = 80/LA

IJ.V2

Line Regulation of
Reference Voltage on Pin 2

VMIN ~ Y,N ~ VMAX

RA

Resistance on Pin 3 to Ground

(Note 4)

Output Voltage Tolerance

Feedback Resistor Rf Tol. ± 1%

10

1.7

60

= 3.0V)
100% Duty Cycle (VS = OV)

V
V

60

= 100V

V
V

0.9

Y,N

. VOUT

V

6

V

/LA
rnA

26

rnA
2.7

V
V

0.9

V

5

mV

4.0

kn

4

9

%

V4

Voltage Swing-Pin 4

3.0

V

14

Charging Current-Pin 4

330

/LA

IClK

Clock Input Current-Pin 6

VClK

= 3.5V

tr

Transistor Current Rise Time

2.0A (Note 6)

70

ns

7.0A (Note 6)

120

ns

tf

Transistor Current Fall Time

2.0A (Note 6)

100

ns

7.0A (Note 6)

160

ns

7.0A (Note 6)

120

ns

7.0A (Note 6)

600

ts

Diode Storage Time

I(j

Delay Time

=
10 =
10 =
10 =
10 =
10 =

fMAX

Max Clock Frequency

(Note 5)

ZPIN1

Impedance at Pin 1

(Note 6)

'Ij

Efficiency

VOUT = 5V
lOUT = 1A

9JC

Thermal Resistance

10

1.75

4

ns
200

Ifo = 25 kHz (Note 6)
Ifa = 200 kHz (Note 5)

(Note 1)

3-8

rnA

kHz

5

Mn

80

%

70

%

4.0

·C/W

Electrical Characteristics (Continued)
Note 1: 8JA is typically 3S'C/W for natural convection cooling.
Note 2: VOUT and lOUT refer to the output DC voltage and output current of a switching supply after the output LC filter as shown in Figure 1.
Note 3: Quiescent current depends on the duty cycle of the switching translator.
Note 4: This test includes the input bias current of the error amplifier.
Note 5: Circuit configured as shown In Figure 1.
Note 6: These parameters are not tested. They are given for Informational purposes only.
Note 7: FuncUonally tested at limits only (pass·fail).
Note 8: A military RETS specification is available upon request. At the time of printing. the HS7067 RETs specificaUon complied with the Min and Max limits in this
table. The HS7067K may also be procured as a Standard Military Drawing.

Typical Performance Characteristics
Frequency vs Timing
Capacitance

Power Derating Curve

lM~.

25

.e

100

... I"-

3OOkl=Sa

20

!:

Typical Compensation
Input Voltage vs Rc

15

"'-

g:l00k'I~1
1=

10

.s

oL-..L--'--'--'--"'=-----'
o 25 50 75 100 125 150 175
AMBIENT TEMPERATURE ('C)

6JO =
6JA =

4 C/W
35DC/W

10k L-..........................--'-'-...........
100
1000
10000
CT-TlMfNO CAPACITANCE (pF)

roo
10
20k

2k
RC(D)

TL/K/S74S-3

1

D

fO = 10k x

,

Cr

Typical Applications
THE BUCK CONVERTER (Step Down)
The buck converter is the most common application in
switching-power conversion. It provides a step-down of voltage with a minimum ,of components and a maximum of efficiency (for further information on the theory of operation of
a buck converter, see AN-343). The complete circuit is
shown in Figure 1.

fO

25kHz

200kHz

L

86/-tH

21/-tH

CT

0.0039/-tF

330pF

Co

0.2/-tF

0.068 /-tF

Rt

4kO

4kO

Ro

5.7kO

5.7kO

COUT

1500/-tF

680 JLF

VIN = tOV to 35V
VOUT = 5V
lOUT = tA to 6A

Load Regulation = 40 mV
Line Regulation = 5 mV

TL/K/6746-4

FIGURE 1. Buck (Step-Down) Converter

3-9

~ ~--------------------------------------------------------------------------------,

~

en

:z::

Typical Applications (Continued)
Design equations:
Following are the design equations for a buck converter application using the HS 7067:

CapaCitor losses (Pel
P = ESR x (Vo (T - DTl)2
C
4l

1
CT = 104 X fo

Diode DC losses (Po)
Po = Vf X 10 X (1 - D)

lMIN = (VIN(MAX)-VO) Vo
VIN(MAX) x fo x 06.1

(Note 7, 9)

C
06.1
MIN - 4fo(eo - 06.1 x ESR)

(Note 8, 9)

Drive Circuit losses (DO
DL = 0.02 X VIN X 0

Cc =

Inductor losses (PLl
PL = 102 X RL (DC winding resistance)

bOlc
Rc

Power Output (Po)

Rc = 2x10 5
VIN(MAX)
Rf = 4k(VO -2.5
2.5

Po = «VIN - Vs) toN) - «VF) toFF) x 10
tON + toFF

)0

Efficiency (7/)
Po

operation.

TRANSFORMER COUPLED CONVERTERS
In addition to the implementation of a buck converter, the
HS 7067 can be used in various transformer coupled configurations. They can be used in various topologies such as:
step-up, step-down, inverter, multiple outputs and isolated
converters.
There are basically two different methods in implementing
transformer coupled converters: the flyback and the foward
topology.

Nole 8: CMIN is the minimum value of output filter capacitance, C, necesESR is the Effective
sary to achieve an output ripple vollage,
Series Resistance of the output filter capacHor, C, at the operating

eo.

frequency,

fo.

=

Peak to Peak Ripple current through the inductor and the
.
<1.1
<1.1
capacitor.
< 10MIN and < 7- 10MA)(·

Nole 9: <1.1

'2

'2

Efficiency Equations
Since high efficiency is the principal advantage of switchedmode power conversion, switching regulator losses are an
important deSign concern. losses and efficiency of a buck
converter can be calculated with the following equations.
10 is the load current, and is the average output current at
pin 8.

The Flyback Principle
Figure 2 shows a functional diagram of a flyback converter.
Depending on the turn ratio N21N1 and the feedback voltage, it can be implemented as a step-down or step-up converter.

Switching Period (T)

When the switch is on, the current (ip) flows through the
primary winding creating a magnetic flux in the core and
storing the energy. At this time, the voltage at the secondary
keeps the same polarity (with respect to the dotted terminals), the diode is off and no current flows through it. When
the switch is off, the voltage at the secondary and primary
becomes reversed and the diode turns-on (Id)' The stored
energy is then transferred to the load and the output filter
capaCitor. The energy stored in the capacitor will supply the
load current during the next turn-on.

1
T=-=tON+tOFF
fo
Duty Cycle (D)
D=_...::to""N_
toN + toFF
Transistor DC losses (PT)
PT = Vs x 10
Transistor Switching losses (Ps)
Ps = (VIN + VF)

x

Po

7/=~=~+~+~+~+~+~+~

Note 7: LMIN is the minimum value of output filter Inductance, L, for stable

x 0

10 X (tr + tf ; 2ts) fo

TLlK/6746-5

FIGURE 2. typical Flyback Functional Diagram

3-10

Typical Applications (Continued)

TON

,

TOFF

,

f--'

VI

Vp

~

= Voltage across the switch

Vs

~

Voltage at the secondary

Ip

~

Current at primary

Id

~

Current through diode

Ie

~

Current through output cap

lout

= Output current of the converter

Dol

~

o

~ Ton/(Toff

F

~

Switching frequency

Vdf

~

Forward voltage drop of the diode

V1

~ Vout X N1JN2

V3

= Saturation voltage of the switch

V4

~ Vou'

Vdf

V2 ~ Vin

+

LJ .
t

r1 r1
U u=

::p

Ton)

.,......
'--

IpEAK ~
IBIAS

Ripple current

,

t

--

'n

Vas

+

i--

'::b u

Voltage at primary

+

T=I/F

Vs

Vou' N1JN2

'1 D D r,

Vs = Vin X N2JN1

m

t

e

Fl

Fl

.
TUKl6746-6

FIGURE 3. Typical Flyback Waveforms

The Forward Principle

The load current is not supplied directly by the input source
when the switch is on, but only by the energy stored in the
output capacitor. The output voltage is monitored by the
feedback loop which controls the duty cycle (0) through the
PWM (Pulse Width Modulator) which in turn, modulates the
amount of energy being transferred from the input to the
output. Figure 3 shows the waveforms of a continuous
mode flyback converter (primary current Ip is OC biased).

The forward converter is a little more complex and requires
more components than the flyback, but the output ripple
voltage is smaller. Rgure 4 shows a simplified diagram of a
forward converter.
When the switch turns·on, a voltage Vs = V1 X N2/N1
appears at the secondary of the transformer. The diode 02

TUK/6746-7

FIGURE 4. Typical Forward Functional Diagram

3·11

functional principle of the demagnetizing winding is similar
to the flyback in the sense that, during the turn-off time, the
residual magnetism will generate a reverse voltage at the
demagnetizing winding (with respect to the dotted terminals)
turning on the diode Os.
In the forward mode, when the switch is off, the load current
is supplied by the energy stored in the output capaCitor and
the choke inductor but when the switch is on, it is supplied
by the input source through the transformer. This accounts
for the lower output ripple voltage.

Typical Applications (Continued)
is off while 01 turns-on, allowing the current to flow through
the inductor L (ldl and Ill, storing energy in its core, and
supplying the load current (lout> and the capacitor current
(Iel at the same time. When .the switch turns-off, the magnetic energy stored in the core of the inductor creates a
current (ld21 which flows through the diode 02. The load
current lout therefore, equals to Id2 + Ie.
During the "off" time of the switch, some residual magnetism will stay in the core of the transformer and has to be
removed before the next cycle, so that it does not accumulate, leading to core saturation.

The output voltage is monitored by the feedback loop,
which controls the duty cycle through the PWM, which in
turn modulates the amount of energy being transferred from
the input to the output.

A demagnetizing winding is used to "dump" the residual
energy back to the input or output of the converter. The

TD

Vp
VIN
Vp

va.
V.
Ip
Idl
Id2
Ida
IL
Ie
lout
41

F
0
VI
V2
V4
Vs

= Voltage at primary
= Voltage across the switch
= Voltage at secondary
= Current at primary
= Current through diode 01
= Current through diode 02

TOFF

~"""-'-"""I'

I

I

I--

VI

TON

-.

__ U

I
I
I
I

T=I/F

-.

rU

r-U r

(]

(]

I

I

I

t

= Current through diode Oa

= Current through Inductor L
= Current through output cap
= Output current of the converter
= Ripple current
= Switching frequency
= Ton I (Toff + Ton)
=Vln X NIlNa
V3

(] .
t

= Vln

= Vln + VI
= Saturation voltage of the switch
= Vln X N2INI
Va = Vln X N2/Na

n

n

c

(]

(]

(]

0

Figure 5 shows the waveforms of the forward converter.
When the switch is off, Vas = Vin + (Vin X N1INS) during
the demagnetization time (Td) and then, drops to Vas = Vin
as indicated in Figure 5.

~=-

ill -

'""""'"

---

0

'-.:;;0>'

........

•t

•t

'-.:;;0>' < ' .
TLlK/6746-6

FIGURE 5. Typical Forward Waveforms

3-12

.-----------------------------------------------------------------------.%

U)

Typical Applications (Continued)
With both flyback and forward topologies, it is possible to
design an inverting converter by using an external op-amp
(Figure 6).

~;_)lIr·····

"'-

Il"

1~

~

Isolated Flyback Converter

~

Figure 8 shows an isolated flyback converter using a sense
winding for feedback. Although, in practice the line regulation is acceptable, the load regulation can be marginal if the
coupling between the windings is poor. However, the sense
winding cannot detect any ohmic voltage drop in the main
output so, a heavier gauge wire should be used to reduce
this regulation error. Also, the sense winding will not sense
the non-linear voltage drop across the diode, and this accounts for most of the load regulation inaccuracy. Therefore, the sense winding method is only recommended for
applications where load variations are small.
Figure 8 shows an isolated flyback converter with an output
of 5V at 2A. The input voltage range is from + 1OV to
+40V. The output can be adjusted to +5V by using the
5 kG trimpol.

TLlK/6746-10

Performance Data

FIGURE 6

Parameter

Flyback Step-Up Application
Figure 7 shows flyback converter in a step·up mode where
an Input voltage of + 12V to + 30V will be converted into a
regulated output voltage of + 50V.

Conditions

Result

Efficiency

Vout = 5V@2A
Vin = 30V

75%

Line Regulation

Vout = 5V@2A
10V S; Vin S; 40V

5%

Load Regulation

Vin
1A

Performance Data
Parameter
Efficiency

Conditions

Result

Vout = 50V@300mA
Vin = 15V

82%

Line Regulation

Vout = 50V @300 mA
12V S; Vin S; 30V

0.2%

Load Regulation

Vin = 15V
Vout = 50V
50 mA S; lout

0.2%
S;

30V
lout S; 2A

7%

Isolated Forward Converter
As described previously, forward converters exhibit lower
output ripple voltage and the opto-coupler feedback
scheme provides good regulation as well as input to output
isolation.
An opto-coupler feedback is usually difficult to implement
because the transfer function of the opto-coupler is non-linear, the current transfer ratio changes with time and temperture and also from one unit to another. Figure 98 shows the
circuit diagram of a 5V @ 3A power converter with an input
voltage range of + 14V to + 30V using an Isolated forward
topology.

300 mA

....-.I-.. . . . .

12V TO 30V

330 p.Y

=
S;

1 NY

SOV
@300mA

....- - -...-.OV

= Unitrode UES1302
T = Pulse Engineering PE64428
10 = 100 kHz
o

lout (min) = 50 rnA

• ELECTROLYTIC CAPACITOR
TLlK/6746-11

FIGURE 7. Flyback Step-Up Converter

3-13

Typical Applications

(Continued)

01
=
02
=
lout (min) =
fo
=
T
=

International Rectifier 50S0060
lN4148
IA
100 kHz
Transformer made of a core Fenoxcube 181 1PA2503B7
Primary
= 8 turns with 5 strands ;1129
Secondary = 6 turns with 15 strands ;1130
Sense
= 25 turns wilh 1 strand .. 30
windings should be Interleaved In order to Improve
the coupling and regulation.

33kll

t--I~"",,-5V
02A

10V TO 40V

330",F

..-----.4....... 0V

I NF

.1311
2W

FIGURE 8. Isolated Flyback Converter

• ELECTROLYTIC CAPACITOR

TLlK/6746-12

01
03
T

= 02 = International Rectifier 5080060
= Unilrode UESI302

L

= Pulse Engineering PE52711
= 50 kHz

fo
lout (min)

= Pulse Engineering PE64423
=

0.5A
=L

330",F

..----4~-----~--~~

2NF
3kll

45.3 kll

• ELECTROLYTIC CAPACITOR

FIGURE 9a. Isolated Forward Converter

TVK/6746-13

TL/K/6746-9

Figur9 9b shows Ihe typical forward converter waveforms in continuous mode which can be observed using the circuli from Rgurs 9a. Top waveform Is the voltage
across the switch (20Vldiv). Bottom waveform is Ihe currenllhroughoul the swllch (IA/div). Horizonlal Scale = 5 !'s/div. Yin = 20V; Vout = 5V @ 3A.

FIGURE9b.

3-14

Typical Applications

(Continued)

An LM385Z (adjustable reference) is used as a comparator
and error amplifier. This reference always wants to maintain
1.2V between pins 1 and 2 and will draw as much current as
necessary from the opto-coupler to achieve this. Therefore,
the feedback loop is virtually independent of the gain of the
opto-coupler.
Performance Data

TL/K/6746-16

Conditions

Result

Efficiency

Vout = 5V@3A
Yin = 30V

78%

Line Regulation

Vout = 5V@3A
14V ,s; Yin ,s; 30V

0.1%

FIGURE 12. Current Limit Circuitry
The sense resistor should be a low inductance type, otherwise the series inductance creates a high impedance at
transients and activates the shutdown Circuitry. If such a
resistor cannot be found, a 0.1 ,...F connected in parallel with
it will compensate the series inductance.

Load Regulation

Vout = 5V
Yin = 20V
0.5A ,s; lout ,s; 3A

0.1%

When such a circuitry is used, the duty cycle limiting diode
becomes optional, but the soft start capacitor should still be
at least 10 ,...F.

Parameter

DECOUPLING AND GROUNDING
Special attention should be given to the decoupling of the
HS 7067 itself at the input (pin 5), where the capacitor must
be at least 100 ,...F and connected as close to the device as
possible. Large switching spikes at the input of the pass
transistor can cause breakdown of the junction and destroy
the device. (See Figure 13.)
The waveform at the top of the picture represents the voltage across the switch of a typical BUCK (step down) converter. When the switch is turned off, the current in the inductor falls to zero (see waveform at the bottom) and a
switching spike occurs across the switch. This spike can
reach several tens of volts on top of the normally expected
voltage across the switch and lead to stress on the device if
the overall voltage exceeds the maximum rating.
The picture below shows a spike of about ten volts with a
330 ,...F capacitor of average quality.

Application Hints
DUTY CYCLE LIMITING
In a f1yback converter, the error amplifier sees OV at the
output of the converter during the initial turn-on, and forces
the duty cycle to 100% until it sees the output voltage rising
to the final value; but no voltage will appear if the switch
does not turn off (see flyback principle). The result is that
the core will saturate, reducing the effective impedance of
the transformer to about on, and destroying the pass transistor. To prevent this, the duty cycle must be limited to a
value at which the core does not saturate. A diode connected between pins 1 and 2 (Figure 11), will limit the duty cycle
to about 80%.

VOLTAGE ACROSS
PIN5&PIN8
TL/K/6746-15

FIGURE 11. Duty Cycle Limiting Circuit
SOFT START
For any converter, connecting a large capacitor (20 to
200 ,...F) between pin 2 and the case is recommended to
allow the reference voltage to slowly reach its final value
after start-up. This allows the HS 7067 to start-up smoothly
and minimizes the inrush current. The time constant can be
calculated by:
T = 103 X C

CURRENT
THROUGH
SWITCH
VERTICAL SCALE: 20 VOLTS/DIV
HORIZONTAL SCALE: 2 ,.S/DIV
TUK/6746-17

FIGURE 13

It is always a good practice to incorporate soft start and duty
cycle limiting when designing a switching power converter,
especially when a current limit circuitry is not utilized.

The reference voltage (pin 2) must be decoupled with at
least 10 ,...F and the compensation network (pin 1) should
be decoupled with a ceramic capacitor of 1 nF to 10 nF.
Switching noise on the reference voltage pin (pin 2) or on
the compensation pin (pin 1) can create different types of
oscillations and instabilities.
Because of the high current and high voltage capability of
the HS 7067 a single pOint grounding or, at least a grounding where the force ground is separated from the circuit
ground, is highly recommended.

CURRENT LIMIT
The schematic in Figure 12 shows how to protect the pass
transistor against excessive current, by sensing the current
through a series resistor, and shorting the PWM control voltage at pin 1 to ground, using transistor 2N5772 (this is made
possible by the 5 Mn output impedance of the error amplifier), which will cause the pass transistor to turn off.

3-15

o ,------------------------------------------------------------------.
~

CD
....
~National
::z:::

...I

~ Semiconductor

::z:::

LH 1605/LH 1605C
5 Amp, High Efficiency Switching Regulator

U;
....~

...I

General Description

Features

The LH1605 is a hybrid switching regulator with high output
current capabilities. It incorporates a temperature-compensated voltage reference, a duty cycle modulator with the
oscillator frequency programmable, error amplifier, high current-high voltage output switch, and a power diode. The
LH1605 can supply up to 5A of output current over a wide
range of regulated output voltage.

•
•
•
•
•
•

Step down switching regulator
Output adjustable from 3.0V to 30V
5A output current
High efficiency
Frequency adjustable to 100 kHz
Standard B-pin TO-3 package

Block and Connection Diagrams

INPUT

5

8

Case Is Ground

OUTPUT

SlEERING
DIODE
(ANODE)

7

N.C.

OUTPUT
DIODE

VREf

N.C.

CASE
GROUND
TL/K110114-2

3
TIMING
CAPCr

4

ERROR
AMPLIFIER
INPUT

EXT. CAP.
(VREf')
TL/K/l0114-1

3-16

Top View

Order Number LH1605K or
LH1605CK
See NS Package Number K08A

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
35Vmax
Input Voltage (VIN)
Output Current (10)
6A
Operating Temperature (TJ)
150'C
Internal Power Dissipation (Po) (Note 1)
20W
Operating Temperature (TA)
LH1605C
-25'Cto +85'C
LH1605
-55'Cto + 125'C

Electrical Characteristics Te =
Symbol

Characteristics
Output Voltage Range

60V
6A

25'C, VIN = 15V, VOUT = 10V unless otherwise specified
LH1605

Conditions
Min

VOUT

-65'C to + 150'C
20% to 80%

Storage Temperature Range (TSTG)
Duty Cycle (D.C.)
Steering Diode Reverse Voltage
(VR) (VS-7)
Steering Diode Forward Current
(10) (17-S)

VIN ~ Vo +5V

Typ

3.0

LH1605C
Max

Min

30

3.0

Typ

Units
Max
30

10= 2A

(Note 2)
Vs

Switch Saturation Voltage

Ie = 5.0A
Ie = 2.0A

1.6
1.0

2.0
1.2

1.6
1.0

2.0
1.2

VF

Steering Diode On Voltage

10 = 5.0A
10 = 2.0A

1.2
1.0

2.8
2.0

1.2
1.0

2.8
2.0

5.0

0.1

5.0

V

VIN

Supply Voltage Range

IR

Steering Diode Reverse Current

VR = 25V

0.1

IQ

Quiescent Current

lOUT = 0.2A

20

20

mA

V2

Voltage on Pin 2

2.5

2.5

V
ppml"C

10

35

35

10

p.A

t"v2 11H

V2 Temperature Coeff.

100

100

V4

Voltage Swing-Pin 4

3.0

3.0

V

14

Charging Current-Pin 4

70

70

p.A

RA

Resistance Pin 3 to GND

2.0

2.0

kn
ppm/'C

aRA/aT

Resistance Temp. Coeff.

75

75

tr

Voltage Rise Time

lOUT = 2.0A
lOUT = 5.0A

350
500

350
500

tf

Voltage Fall Time

lOUT = 2.0A
lOUT = 5.0A

300
400

300
400

Is

Storage Time

td

Delay Time

Po

Power Dissipation

'Ij

Efficiency

lOUT = 5.0A
VOUT = 10V
lOUT = 5.0A

1.5

1.5

","S

100

100

ns

16

16

W

75

75

5.0
5.0
Thermal Resistance (Note 1)
Nolo I: 8JA Is typically srrc/w for natural convection cooling.
Nole 2: Vour refers to the output voltage range of switching supply after the output LC filter as shown In the Typical Application circuit.

8Je

3-17

ns

%
'C/W

~
.....
en
o

U1
.....
r::::E:
.....

g

n

0II)

-........
CI
CD

67

::J:

5

+

II)

-

LHI605

IN

~H

--

OUT

+

RS 2k

+

CI
CD

....::J:

TLlK/l0114-3

Minimum V,N - VOUT = 5V for Proper Operation
R _ 2
S -

x 1()3 (YOUT - 2.5)

Y,N = 10 - 1BY
YOUT = 5Y
lOUT = 3A (Max)
lOUT = 1A (Min)
1j "" 70%

2.5

Load Reg. = 50 mY
Line Reg. = 10 mY
Ripple = 20 mY

Frequency vs Timing
Capacitance

Power Derating Curve
25r--r--~~--~--~~

g

lOOk

w~~~~~~~+--1

"-

~ 15r--+--+-~~~--r-~

'r-..,

~ 10r--+--+-~--~--r-~

i

O~~--~~--~~~

o

25

50

75

100

125

loOk

100

ISO

1,000

Cr -

AMBI£NT TEMPERATURE (OC)
TLlK/l0114-4

TL/K/l0114-5

Design Equations
. .
POUT X 100
EffiCiency (1j) = ~~....:....;~
P,N
Transistor DC Losses (Pr) = lOUT X Ys (

Diode DC Losses (Po) = lOUT X YF (

tON

toN
)
+ tOFF

toFF
)
tON + tOFF

Drive Circuit Losses (DLl = YIN02 X
toN
30
toN + toFF
Switching Losses Transistor (Ps) = Y,N X lOUT X 2( tr + tf
toN + tOFF
Transistor Duty Cycle

Diode Duty Cycle =

=

tON

toN
+ tOFF

= YOUT
Y,N

tOFF
= 1 _ YOUT
toN + toFF
Y,N

Power Inductor (PLl = 10m2 x RL (Winding Resistance)
Efficiency (1j) =

YOUTIOUT

YOUTIOUT

10,000

TIMING CAPACITOR (pF)

+ PT + Po + DL + Ps + PL

3-1B

X 100%

~National

~ Semiconductor

LM1524D/LM2524D/LM3524D
Regulating Pulse Width Modulator
General Description
The lM1524D family is an improved version of the industry
standard lM1524. It has improved specifications and additional features yet is pin for pin compatible with existing
1524 families. New features reduce the need for additional
external circuitry often required in the original version.
The lM1524D has a ± 1% precision 5V reference. The current carrying capability of the output drive transistors has
been raised to 200 mA while reducing VCEsat and increasing
VCE breakdown to 60V. The common mode voltage range
of the error-amp has been raised to 5.5V to eliminate the
need for a resistive divider from the 5V reference.
In the lM1524D the circuit bias line has been isolated from
the shut-down pin. This prevents the oscillator pulse amplitude and frequency from being disturbed by shut-down. Also
at high frequencies ('" 300 kHz) the max. duty cycle per
output has been improved to 44% compared to 35% max.
duty cycle in other 1524s.
In addition, the lM1524D can now be synchronized externally, through pin 3. Also a latch has been added to insure

one pulse per period even in noisy environments. The
lM1524D includes double pulse suppression logic that insures when a shut-down condition is removed the state of
the T-flip-flop will change only after the first clock pulse has
arrived. This feature prevents the same output from being
pulsed twice in a row, thus reducing the possibility of core
saturation in push-pull designs.

Features
• Fully interchangeable with standard lM1524 family
• ± 1% precision 5V reference with thermal shut-down
• Output current to 200 rnA DC
• 60V output capability
• Wide common mode input range for error-amp
• One pulse per period (noise suppression)
• Improved max. duty cycle at high frequencies
• Double pulse suppression
• Synchronize through pin 3

Block Diagram
REFERENCE
16
....----1REGULATOR
1--_";';"OVREf

VIN ~;;"""--1----------------

5V TO
INTERNAL CIRCUITRY

INV INPUT
NIINPUT

9
COMPENSATION o - - - - - - - - - i - - I

+ CL5ENSE
- CL5ENSE

EMITTER A
10

1 k.!l

SHUrooWNo--~~~~~-i

JUUL

Cr~7-:~.....:-=-=:....---~C~::JI-J_-----------......:3~:rLATOR

r

RT

GND
TLiH/BB5D-l

3-19

Absolute Maximum Ratings (Note 5)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage
40V

Operating Junction Temperature Range (Note 2)
-55·Cto
LM1524D
-40·C to
LM2524D
O·C to
LM3524D

+ 150"C
+ 125·C
+ 125·C

Collector Supply Voltage
(LM1524D)
(LM2524D)
(LM3524D)

Maximum Junction Temperature
Storage Temperature Range

+ 150·C

60V
55V
40V

Output Current DC (each)

150·
- 65·C to

Lead Temperature (Soldering 10 sec.) J Pkg.
Lead Temperature (Soldering 4 sec.) M, N Pkg.

300·C
260·C

200mA
5mA

Oscillator Charging Current (Pin 7)
Internal Power Dissipation

1W

Electrical Characteristics (Note 1)
LM1524D
Symbol

Parameter

Conditions

Typ

LM2524D

LM3524D

Tested Deelgn
Tested Design
Tested Design
Limit
Limit Typ Limit
Limit Typ Limit
Limit
(Note 3) (Note 4)
(Note 3) (Note 4)
(Note 3) (Note 4)

Units

REFERENCE SECTION
VREF

Output Voltage

4.95
5

4.85

4.90
5.05

5.10
VRLlne

Line Regulation

aVIN
Ripple Rejection I
aVREF
los

= 8Vt040V
= OmAt020mA

VIN

VRLoad Load Regulation IL

= 120Hz

VREF

Output Noise

10Hz~l~

Long Term
Stability

TA

5.20

5.25

VMax

10

15

30

10

25

50

mVMax

15

10

15

25

10

25

50

mVMax

66
25

66
25

50

20

mAMin

50
180

100

dB
25

50

40

= 125·C

5.15

20

66

10kHz

VMln

5

150
No

4.75
5

10

=0

Short Circuit
Current

4.80

5

40

200
100

20

40

rnA Max
100

p.Vrms Max

20

mV/kHr

350

kHzMin

OSCILLATOR SECTION
lose

Max. Freq.

RT = 1k, CT
(Note 7)

= 0.001 p.F

lose

Initial
Accuracy

RT = 5.6k, CT
(Note 7)

= 0.01 p.F

RT = 2.7k, CT
(Note 7)

= 0.01 p.F

550

500

550

18.5
20

17.5
20

alosc
alesc

Freq. Change
with Temp.

TA = -55·Cto + 125·C
at 20 kHz RT = 5.6k,
CT = 0.01 p.F

0.5

Vesc

Output Amplitude RT
(Pin 3) (Note 8)

= 5.6k, CT = 0.01 ,..F

tpw

Output Pulse
Width (Pin 3)

= 5.6k, Cr = 0.01

RT

p.F

kHzMin

22.5

22.5

kHzMax

36

34

30

kHzMin

46

kHzMax

1.0

"loMax

38
40

= 8t040V

VIN

17.5
20

21.5
38

Freq. Change
withVIN

500

38
42

0.5

1

5

1

5

0.5

5

%

3

2.4

3

2.4

3

2.4

VMin

0.5

1.5

0.5

1.5

0.5

1.5

p.sMax

3-20

Electrical Characteristics (Continued)
LM1524D
Symbol

Parameter

LM2524D

LM3524D

Tested Design
Tested Design
Tested Design
Units
Typ Limit
Limit Typ Limit
Limit Typ Limit
Limit
(Note 3) (Note 4
(Note 3 (Note 4
(Note 3 (Note 4

Conditions

OSCILLATOR SECTION (Continued)
Sawtooth Peak
Voltage

Rr

=

5.6k, Cr

=

0.Q1 /LF

Sawtooth Valley
Voltage

Rr

=

5.6k, Cr

=

0.01 /LF

3.4

3.6

3.4

3.6

3.8

3.8

VMax

1.1

0.8

1.1

0.8

0.6

0.6

VMin

0.5

5

2

8

10

2

10

mVMax

1

5

1

8

10

1

10

/LAMax

0.5

1

0.5

1.0

1

0.5

1

/LAMax

65

/LAMin

ERROR·AMP SECTION
VIO

Input Offset
Voltage

VCM

=

2.5V

liB

Input Bias
Current

VCM

=

2.5V

110

Input Offset
Current

VCM

=

2.5V

lcosl

Compensation
Current (Sink)

VIN(I) - VIN(NI)

Icoso

=

75

150 mV

65

95

Compensation
Current (Source)

VIN(NI) - VIN(I)

RL

=

150 mV

95
115

125

125

/LAMax

-115

-125

-125

/LAMin

-95

-95
-75

=

AVOL

Open Loop Gain

VCMR

Common Mode
Input Voltage Range

CMRR

Common Mode
Rejection Ratio

GBW

Unity Gain
Bandwidth

AVOL

Vo

Output Voltage
Swing

RL

=

PSRR

Power Supply
Rejection Ratio

VIN

=

00,

VCM

=

2.5V

80

=

0 dB, VCM

=

2.5V

80

80

90

3

8to40V

-65

74

60

1.5
5.5

1.4
5.4

80

80

80

90

3
0.5
5.5

00

-95
-65

74
1.5
5.5

90

95

80

70

/LAMax
60

dBMin

1.5
5.5

VMin
VMax

70

dBMin

2
0.5
5.l)

76

70

MHz
0.5
5.5

VMin
VMax

80

65

dbMin

COMPARATOR SECTION
Minimum Duty
Cycle

Pin 9 = 0.8V,
[Rr = 5.6k, Cr

=

0.Q1 /LFI

tosc

Maximum Duty
Cycle

Pin 9 = 3.9V,
[Rr = 5.6k, Cr

=

0.Q1 /LFI

toN
tosc

Maximum Duty
Cycle

Pin 9 = 3.9V,
[Rr = 1k, Cr

toN
tosc
toN

=

0.001 /LF]

VCOMPZ Input Threshold
(Pin 9)

Zero Duty Cycle

VCOMPM Input Threshold
(Pin 9)

Maximum Duty Cycle

liB

Input Bias
Current

0

0

0

0

0

0

%Max

49

47

49

45

49

45

%Min

44

40

44

35

44

35

%Min

1

1

1

V

3.5

3.5

3.5

V

-1

-1

-1

/LA

3-21

Electrical Characteristics (Continued)
LM1524D
Symbol

Parameter

Conditions

LM2524D

LM3524D

Tested Design
Tested Design
Tested Design
Units
Limit Typ Limit
Limit Typ Limit
Limit
Typ Limit
(Note 3) (Note 4)
(Note 3) (Note 4)
(Note 3) (Note 4)

CURRENT LIMIT SECTION
VSEN

Sense Voltage

V(Pin2) - V(Pln1) ~
150mV
200

190

180
200

210
TC-Vsense Sense Voltage T.C.
Common Mode
Voltage Range

Vs - V4 = 300 mV

180

mVMln

220

mVMax

200
220

0.2

0.2

0.2

mV/"C

-0.7
1

-0.7
1

-0.7
1

VMin
VMax

SHUT DOWN SECTION
Vso

High Input
Voltage

V(Pin 2) - V(Pln 1) ~
150mV

1

Iso

High Input
Current

I(pin 10)

1

0.5
1.5

1

0.5
1.5

1

0.5
1.5

1

1

VMln
VMax
mA

OUTPUT SECTION (EACH OUTPUT)
VCES

Collector Emitter
Ic"; 100 p.A
Voltage Breakdown

ICES

Collector Leakage
Current

VCE = 60V

60
0.1

Saturation
Voltage

VMin

50
0.1

VCE = 55V

50

VCE = 40V
VCESAT

40

55

p.AMax
0.1

50

IE = 20mA

0.2

0.4

0.2

0.5

0.2

0.7

Ie = 200mA

1.5

2.2

1.5

2.2

1.5

2.5

18

17

18

17

18

17

VMax

YEO

Emitter Output
Voltage

IE = 50mA

tR

Rise Time

VIN = 20V,
IE = -250 p.A
Rc = 2k

200

200

200

ns

Rc = 2k

100

100

100

ns

Fall Time

tF

VMin

SUPPLY CHARACTERISTICS SECTION
VIN

Input Voltage
Range

T

Thermal Shutdown (Note 2)
Temp.

liN

Stand By Current

After Turn-on

VIN = 40V (Note 6)

8
40

8
40

160
5

160
10

5

8
40
160

10

5

VMin
VMax
'C

10

mA

Nole 1: Unless otherwise stated, these specifications apply for TA = TJ = 25'C. Boldface numbers apply over the rated temperature range: LM15240 is - 55'C to
125'C, LM2524D Is -40' to 85'C and LM3524D Is O'C to 70'C. VIN = 20V and fose = 20 kHz.
Nole 2: For operation at elevated temperatures, devices In the J package must be derated based on a thermal resistance of 132'C/W,lunction to ambient, and
devices In the N package must be derated based on a thermal resistance of 86'C/W,Iunction to ambient. Devices in the M package must be derated at 12S'C/W,
junction to ambient.
Nole 3: Tested IImHs are guaranteed and 100% tested in production.
Nole 4: Design limits are guaranteed (but not 100% production tested) over the Indicated temperature and supply voltage range. These limits are not used to
calculate outgoing quality level.
Nota 5: Absolute maximum ratings Indicate limits beyond which damage to the device may occur. DC and AC electrical specHications do not apply when operating
the device beyond Its rated operating conditions.
Nota 8: Pins I, 4, 7, 8,11, and 14 are grounded; Pin 2 = 2V. All other Inputs and outputs open.
Nota 7: The value of a Ct capaCitor can vary with frequency. Careful selection of this capaCitor must be made for high frequency operation. Polystyrene was used In
this test. NPO ceramic or polypropylene can also be used.
Nole 8: OSC amplitude Is measured open circuit. Ava/lable current is IlmHed to 1 mA so care must be exercised to limit capacitive loading of fast pulses.

3-22

,-----------------------------------------------------------------------------'r
....:s::::
Typical Performance Characteristics
Maximum Average Power
Dissipation (J Package)
1.2

1.2

~
iii
C

i,

0JA

g

g

""

0.8
0JA

= 132°C/W

0.&
0.4

~

'\..

,eo 0.2

o
-50 -25

0

25

,..... r-.,

z

!2

~

50

75

"

iiiC

0.&

i,

0.4

\l

2.0

~

~
z

~
~,
!:<

1.5
1.0

I

I~UT = ~OO ~A

i..-

T

o

0

25

o

19.0

~

~

~

~
ill,

100 125

18.&

18.2

_.....

,/

~

-50 -25

0.95

C

so

25

":i'

100

is

75

.9

~

itl

6.0

1;;

5.0

i!

~,
-"'

4.0

.28

50

32

r-- r.... ;-....

50

75

100

125

-50 -25

0

25

50

75

PINS '.4,7.8,",1.4=0

!

210

'"
~

200

25

./

~

....... i'o...

..~

I-- -

50 75 100 125

TA - AMBIENT TEMPERATURE (Oc)

190

,~

~

PINS 3.5.6.9.10.12. 13=OPEN
-50 -25 0

125

Current Limit Sense Voltage

....... 1'-.

V,N = 40V
4.0 lOUT REF = 0 rnA
PIN2=2V

100

TA-AMBIENT TEMPERATURE (OC)

....... 1-0...

36

125

-- -

220

V,N - INPUT VOLTAGE (V)

100

........ ;-....

25

w

3.0
.2.4

25

o
75

7.0

V

0

125

Standby Current
vs Temperature

5.0

.j:Io

Reference Transistor
Peak Output Current

TA - ANBIENT TEMPERATURE (OC)

J

U1

0.9
-SO -25

§,

TA=25 0 C
'oUTREF=OmA

20

~

i

~

I
0

Co)

N

~

-";r=-50mA

~

s::

1.00

..s

.... /

V

C
......
r

VIN = 20V
RT=5.&kA
CT= 0.0011'

TA-AMBIENT TEMPERATURE (oC)

I-- ,....,l=-L

17.8

Standby Current
vsVoltage

16

3.30

1.05

,...,.

V,N =20V

.j:Io

3.35

~

10 20 30 40 50 &0 70 80 90 100

TA- ANBIENT TEMPERATURE (Oc)

12

N

Output Transistor Emitter
Voltage

-

75

'"

N
U1

3.40

TA - AMBIENT TEMPERATURE (Oc)

>w

50

= B6oe/W, N PACKAGE

~

,['..

o

I

-50 -25

i\

,eo 0.2

100 125

0.5 _LT=20mA

>~

~

'r-.,

Output Transistor
Saturation Voltage
2.5

en

z

,~

0JA

c

"~

3.45
PACKAGE

I"

0.8

TA -ANBIENT TEMPERATURE (OC)

~

= 1250 C/W, III

~
.j:Io

Maximum & Minimum
Duty Cycle Threshold
Voltage

Maximum Average Power
Dissipation (N, M Packages)

............

/

-

-

~

180
170
-50 -25

0

25

50

75

100

125

TA - ANBIENT TENPERATURE (Oc)

Switching Transistor
Peak Output Current
vs Temperature
300

":i'

..s

;

-.......
200

u

5

S,
0

.9

100

-so

-25

""- " "0

25

so

75

-

100

125

TA-AMBIENT TEMPERATURE (Oc)

TL/H/8S50-3

3-23

cr------------------------------------------------------------"=I'
N

an

Test Circuit

C')

...
o
:::E

2.
lW

2'
lW

~
:::E

~

o

o..!

...
~
,..

~

:5

CB

12

CA
OSC OUT
VREF
NI
INPUT
2

)

LM1524D/LM2524DIlM3524D
INV
INPUT

COMP

LJ9
2.

O.I.F: :::

13

VIN

~

SHUT
DOWN
10

+CL
SENSE
4

)

)

RT

CT

6

5

2.

.,!!..

GND EA

t-!1-<

6

7

RT

I••

lB.

2.

-CL

SENSE

Ea

::=CT

L .. E+-

GND
TL/H/8650-4

Functional Description
INTERNAL VOLTAGE REGULATOR

If two or more LM15240's must be synchronized together,
the easiest method is to interconnect all pin 3 terminals, tie
all pin 7's (together) to a single CT, and leave all pin 6's
open except one which is connected to a single RT. This
method works well unless the LM15240's are more than 6"
apart.

The LM15240 has an on-chip 5V, 50 mA, short circuit protected voltage regulator. This voltage regulator provides a
supply for all internal circuitry of the device and can be used
as an external reference.
For input voltages of less than 8V the 5V oulput should be
shorted to pin 15, VIN, which disables the 5V regulator. With
these pins shorted the input voltage must be limited to a
maximum of 6V. If input voltages of 6V -8V are to be used, a
pre-regulator, as shown in Figure 1, must be added.

A second synchronization method is appropriate for any circuit layout. One LM15240, designated as master, must
have its RT~ set for the correct period. The other slave
LM15240(s) should each have an RT~ set for a 10% longer period. All pin 3's must then be interconnected to allow
the master to properly reset the slave units.
The oscillator may be synchronized to an external clock
source by setting the internal free-running oscillator frequency 10% slower than the external clock and driving pin 3
with a pulse train (approx. 3V) from the clock. Pulse width
should be greater than 50 ns to insure full synchronization.

VIN
S.5V -BV

_
iSr...

= !:mCT O.OOlllf
100~~.
50 l-J..

~

~C~T~=~0.~00ffl5~IlF~~~~~~~

TL/H/B650-10

'Minimum

=

Co of 10 I'F required for stability.
FIGURE 1

OSCILLATOR

ill

The LM15240 provides a stable on-board oscillator. Its frequency is set by an external resistor, RT and capacitor, CT.
A graph of RT, ~ vs oscillator frequency is shown is Figure
2. The oscillator'S output provides the signals for triggering
an internal flip-flop, which directs the PWM information to
the outputs, and a blanking pulse to turn off both outputs
during transitions to ensure that cross conduction does not
occur. The width of the blanking pulse, or dead time, is controlled by the value of CT, as shown in Figure 3. The recommended values of RT are 1.8 kO to 100 kO, and for CT,
0.001 p.F to 0.1 p.F.

I

I CT= 0.0021lF

C

f

=o.61'~~/-;<;-.;:!-~~I/

~ 10~.~

!E

• •

;::

...
I

IX:

5 10 20

50 100200 500 Ik

OSCILLATOR PERIOD illS)
TL/H/8650-5

FIGURE 2

3-24

Functional Description (Continued)
10

The duty cycle is calculated as the percentage ratio of each
output's ON-time to the oscillator period. Paralleling the outputs doubles the observed duty cycle.

vee= 20V
TA' 25·C

]

50

w
:;

..

;:

~

CI

/'

40

w

...

CI

= 0.4
=

§

I!:
CI

.....,'"

3D

>
I-

20

..,>

0.1

:::0

0.0D4

0.001

0.01

0.D4

CI

0.1

CT fpF)

10
TL/H/B650-6

FIGURE 3

~

~

1.5

ERROR AMPLIFIER

1/

2

L

2.5

3.5

VOLTAGE ON PIN 9 (V)

The error amplifier is a differential input, transconductance
amplifier. Its gain, nominally 86 dB, is set by either feedback
or output loading. This output loading can be done with either purely resistive or a combination of resistive and reactive components. A graph of the amplifier's gain vs output
load resistance is shown in Figure 4.

4
TL/H/8650-B

FIGURE 5
The amplifier's inputs have a common-mode input range of
1.5V-5.5V. The on board regulator is useful for biasing the
inputs to within this range.

CURRENT LIMITING
RL =co

80

RL =1M """

iii

::!!

RL = ~OOk

60

'"
<
<:I
<:I
'"
;:...

40

>

20

co

The function of the current limit amplifier is to override the
error amplifier's output and take control of the pulse width.
The output duty cycle drops to about 25% when a current
limit sense voltage of 200 mV is applied between the + CL
and -CL sense terminals. Increasing the sense voltage approximately 5% results in a 0% output duty cycle. Care
should be taken to ensure the -0.7V to + 1.0V input common-mode range is not exceeded.

'"-...

RL -lOOk
RL • ~Ok

"'

~

i\.

'\

RL = RESISTANCE FROM PIN 9
TO GND

0
10

100

Ik

10k

lOOk

FREIlUENCV (Hz)

OUTPUT STAGES
The outputs of the LM1524D are NPN transistors, capable
of a maximum current of 200 mA. These transistors are driven 180· out of phase and have non-committed open coliectors and emitters as shown in Figure 6.

~

1M

10M
TLlH/8850-7

FIGURE 4

OUTPUT --4.....""""1
DRIVE ..

The output of the amplifier, or input to the pulse width modulator, can be overridden easily as its output impedance is
very high (Zo '" 5 MO). For this reason a DC voltage can
be applied to pin 9 which will override the error amplifier and
force a particular duty cycle to the outputs. An example of
this could be a non-regulating motor speed control where a
variable voltage was applied to pin 9 to control motor speed.
A graph of the output duty cycle vs the voltage on pin 9 is
shown in Figure 5.

E8
TL/H/8650-9

FIGURE 6

3-25

TUH/865D-ll

FIGURE 7. Positive Regulator, Step-Up Basic Configuration (IIN(MAX) = 80 mAl

VMo----i------------~------~~----~__,

HM-+OVo

+

Co

TL/H/885D-12

FIGURE 8. Positive Regulator, Step-Up Boosted Current Configuration

3·26

r-----------------------------------------------------------------------------~ ~

Typical Applications

3!:
....

(Continued)

~
Design Equations

Rr
VIN

= 5 kll (~1)
2.5

RF

PIN 1

Current Limit
Sense Volt

•
INV

5k

5k
LI.l35240

VR

RCL =

VIN

fosc .. - 1-

Ea
Ca

L1

lo(MAX)

L1

N

""o
.....
~

Vol
10 VINfOSC
(VIN - Vol V T2
8 AVoVINLI

o

0

en
~

= 2.5Vo (VIN -

C

~

3!:

N

3!:

RM

t-....-_.-rTT'ln........-oVO

""

~

en

N

""o

VIN

10(MAX) = liN Vo

GNO

01

....

~~~~-4-------

--~---_.--oGNO

RauRNO---------~~--~~~-_.--~

TO "'CL PIN

TO +CL PIN

TUH/BB50-13

FIGURE 9. Positive Regulator, Step-Down Basic Configuration (IIN(MAX) = 80 mAl

Rr
VIN
PIN 1

•

5k

5k

5k

INV

VR

HI

VIN

OSC

Ea

+CL

Ca

"'CL

LI.l35240

CA

Rr

01

Cr

+

GHO

Co

Rr

~--~.........~......................................................~~......................................~...........................~_oGNO

TLlH/8650-14

FIGURE 10. Positive Regulator, Step-Down Boosted Current Configuration

3-27

•

Typical Applications (Continued)
Rr

VIN
5k

De81gn Equations

RF= 5k(1-~)
2.5

PIN 1

5k

•

INV
NI

5k

OSC
+CL
LM3524D
-CL

Rr

Cr
GND

Rr

Cr
GND o-~~-4--~------------~--~--~--4-~GND

TL/H/8650-15

FIGURE 11. Boosted Current Polarity Inverter
BASIC SWITCHING REGULATOR THEORY
AND APPLICATIONS
The basic circuil of a step·down switching regulator circuit is
shown in Figure 12, along with a practical circuit design us·
ing the LM35240 in Figure 15.

The circuit works as follows: 01 Is used as a switch, which
has ON and OFF times controlled by the pulse width modu·
lator. When 01 is ON, power is drawn from VIN and supplied
to the load through L1; VA Is at approximately VIN, 01 is
reverse biased, and Co is charging. When 01 turns OFF the
inductor L1 will force VA negative to keep the current flow·
ing in it, 01 will start conducting and the load current will
flow through 01 and L1. The voltage at VA Is smoothed by
the L1, Co filter giving a clean DC output. The current flow·
Ing through L1 is equal to the nominal DC load current plus
some AIIL which Is due to the changing voltage across it. A
good rule of thumb is to set AILp.p ~ 40% x 10-

VINo---..

TL/H/8850-16

FIGURE 12. Basic Step-Down Switching Regulator

e.OV

1-1'--1--1
FIGURE 13

3·28

TUH/8850-17

r-----------------------------------------------------------------------,r
is:
....
Typical Applications (Continued)
U1
N

Solving the above for L1

.
di
VLT
From the relation VL = L!it, Il.IL '"

L1

~

C
.....
r

L 1 = 2.5 Vo (VIN - Vol
10 VINf

Il.IL+ = (VIN - VoltON. Il.IL- = Vo tOFF
L1'
L1
Neglecting VSAT, Vo, and settling Il.IL + = Il.IL-;

is:

~
~

where: L1 is in Henrys

~

f is switching frequency in Hz

r

Also, see LM157B data sheet for graphical methods of inductor selection.

is:

where T = Total Period

CALCULATING OUTPUT FILTER CAPACITOR Co:

U1
N

The above shows the relation between VIN, Vo and duty
cycle.

Figure 14 shows L1's current with respect to 01 's tON and
tOFF times. This curent must flow to the load and Co. Co's
current will then be the difference between IL' and 10.

IIN(OG) = IOUT(OC) CON

~~OFF)'
~NtoFF) VIN

Po = 10Vo
The efficiency, "/, of the circuit is:

Il.V
= ~ X Il.IL X (tON + tOFF)
oP·PC4
22

10Vo
,,/MAX = -Po = - - - -__-=--=---...,..,.----:-PIN
I (tON) V + (VSAT tON + VOltoFF) I
o T
IN
T
0
=

o forVSAT
~
Vo + 1
---

= Il.IL (toN

4C

= VOl = 1V.

tON

+

~) (!) _(VIN -

_ (1l.1L +) X L1 t
_ (1l.1L -) X L1
(VIN - Vol , OFF Vo

Since Il.IL +

=

0.410L1
(VIN - Vol
Il.IL - = 0.410

2

-

Vo)VoT2 r
BVINCoL1
0

C - (VIN - Vol Vo T2
0BAVoVINL1

=

=

2

_ Vo ( T Il.Vop _p 4CL1

CALCULATING INDUCTOR L 1

(1l.1L +) X L1
toFF = T = (V
V)
IN - Q

+ toFF)

Since Il.IL = Vo(T:- tON) and toN = VvoT
1
~

,,/MAX will be further decreased due to switching losses in
01. For this reason 01 should be selected to have the maximum possible fT, which implies very fast rise and fall times.

tON

~

C

Ico = IL -1 0
From Figure 14 it can be seen that current will be flowing
into Co for the second half of toN through the first half of
tOFF, or a time, toN/2 + tOFF/2. The current flowing for this
time is Il.IL/4. The resulting Il.Vc or Il.Vo is described by:

as 01 only conducts during tON.
PIN = IIN(OC) VIN = (lo(OC» CON

~

where: C is in farads, T is

(1l.1L -) X L1
V

+
0
+ O.4loL1

1
·t h· f
Ing requency

SWI C

Il.Vo is pop output ripple
For best regulation, the inductor's current cannot be allowed to fall to zero. Some minimum load current 10, and
thus inductor current, is required as shown below:

Vo

I
- (VIN - VoltON
o(MIN) 2L1
IL
AIL+=

VA
(COLLECTOR
OF PNP)

(VIN - Vo) toN
L1

I~

~

o~_lo(MIN)

TLiH/8650-18

FIGURE 14

TLiH/8650-19

3-29

•

Typical Applications (Continued)
A complete step-down switching regulator schematic, using
the LM3524D, is illustrated in Figure 15. Transistors 01 and
02 have been added to boost the output to 1A. The 5V
regulator of the LM3524D has been divided in half to bias
the error amplifier's non-inverting input to within its common-mode range. Since each output transistor is on for half
the period, actually 45%, they have been paralleled to allow
longer possible duty cycle, up to 90%. This makes a lower
possible input voltage. The output voltage is set by:
Vo = VNI (1

where VNI is the voltage at the error amplifier's non-inverting input.
Resistor R3 sets the current limit to:
200 mV _ 200 mV _
A
R3
0.15 - 1.3 .
Figure 16 and 17 show a PC board layout and stuffing diagram for the 5V, 1A regulator of Figure 15. The regulator's
performance is listed in Table I.

+ :~),
Ll
500,uH
Vo=5 V
'YY""'\.-; I-Q @10=1 A
f=20k Hz

Rl
5k
RIO

!f

02

R9

R4
5k

'=~

C
101-1r

C3

O.I,uF

R5
5k

I

R2
5k

15
16

2
I

R6
6.5k

6
CI
O.~',,uF

7

11

VREF

VIN

NI

EA

INV

CB

LM3524D

RT

EB

,..
R7
30k

Cr
COMP

12

II"'" I

11

GND

-CL

-:

A~

C5=:-1

13

O.,,uF-~
14

500,uF

-~
~

+CL ,L

9

C2.~

O.Ol,uF

CA

R8
510
... 1

~

01
MR850

..2.

8

GND
R3
0.15
RETURN
TL/H/8650-20
'Mounted to Staver Heatslnk No. V5-1.
01 = 80344
Q2 = 2N5023
L1

=

>40 turns No. 22 wire on Ferroxcube No. K300502 Torrold core.

FIGURE 15. 5V, 1 Amp Step-Down Switching Regulator

3-30

Typical Applications (Continued)
TABLE I
Parameter

Conditions

Output Voltage
Switching Frequency

VIN
VIN

Short Circuit
Current Limit

VIN

Load Regulation

= 10V, 10 = 1A
= 10V, 10 = 1A
= 10V

= 10V
= 0.2 - 1A
6,VIN = 10 - 20V,
to = 1A
VIN = 10V,Io = 1A
VIN = 10V, 10 = 1A
VIN

10

Line Regulation
Efficiency
Output Ripple

Typical
Characteristics
5V
20kHz
1.3A
3mV
6mV
80%
10mVp-p

TL/H/8650-21

FIGURE 16. 5V, 1 Amp Switching Regulator, Foil Side

•
TL/H/8850-22

FIGURE 17. Stuffing Diagram, Component Side

3-31

C

~
::i

....I
.....

C

~

N

::i

....I
.....
C

....~

::i
....I

r----------------------------------------------------------------------,
Typical Applications (Continued)
THE STEP-UP SWITCHING REGULATOR
Figure 18 shows the basic circuit for a step-up switching
regulator. In this circuit 01 is used as a switch to alternately
apply VIN across inductor L 1. During the time, tON, 01 is ON
and energy is drawn from VIN and stored in L1; 01 is reverse biased and 10 is supplied from the charge stored in Co.
When Q1 opens, toFF, voltage V1 will rise positively to the
pOint where 01 turns ON. The output current is now supplied through L 1, 01 to the load and any charge lost from Co
during tON is replenished. Here also, as in the step-down
regulator, the current through L1 has a DC component plus
some all. all is again selected to be approximately 40% of
IL. Figure 19 shows the inductor's current in relation to 01 's
ON and OFF times.

t-....~~~~~~OVo
10

TUHIB650-23

FIGURE 18. Basic Step-Up Switching Regulator

... Vo....- - . ,

Vl

Co/.

OV _ _ _ _

l:::toN----I·Ij4-·--'IoFF-I~---,.

T

.,
TUH18650-24

FIGURE 19

3·32

~--------------------------------------------------------------~r

5:
....
U1

Typical Applications (Continued)
From ~IL =
an

VLT

L' ~IL +

'"

VINtON

L1

FromVo = VIN (1 +

N

~~)

.j:Io

C
......

~

d ~I - = (Vo - VIN)tOFF
L L1

N
U1
N

Since ~IL + = ~IL -, VINtoN = VotOFF - VINtoFF,
and neglecting VSAT and VD1

.j:Io

This equation assumes only OC losses, however "1MAX is
further decreased because of the switching time of 01 and
01.

tON)
Vo '" VIN ( 1 +
tOFF
The above equation shows the relationship between VIN, Vo
and duty cycle.

In calculating the output capacitor Co it can be seen that Co
supplies 10 during tON, The voltage change on Co during this
time will be some ~Vc = ~Vo or the output ripple of the
regulator. Calculation of Co is:

In calculating input current IIN(DC), which equals the inductor's OC current, assume first 100% efficiency:

~ V = 10tON or C = 10tON
o

Co

PIN = IIN(DC) VIN
From Vo = VIN CO:F): toFF =

POUT = 10Vo = 10 VIN ( 1 + -tON)
toFF
for "1 = 100%, POUT = PIN
10 VIN (1 +

t~;F) =

liN (DC) = 10 ( 1 +

.j:Io

C

~Vo

0

~: T

f

toN = T - VIN T = T (Vo - VIN) therefore:
Vo
Vo

t~~)

loT (Vo

C -

This equation shows that the input, or inductor, current is
larger than the output current by the factor (1 + tON/tOFF)'
Since this factor is the same as the relation between Vo and
VIN, IIN(DC) can also be expressed as:
IIN(DC) = 10 (

U1
N

1

where T = tON + tOFF =

IIN(DC) VIN

~
r
5:
(0)

o-

~ VIN)
0_

~Vo

-

'----=-~-'

where: Co is in farads, f is the switching frequency,
~Vo is the pop output ripple

~)

Calculation of inductor L 1 is as follows:
L1 = VINto+N, since during tON,
~IL

So far it is assumed "1 = 100%, where the actual efficiency
or "1MAX will be somewhat less due to the saturation voltage
of 01 and forward on voltage of 01. The internal power loss
due to these voltages is the average IL current flowing, or
liN, through either VSAT or VD1. For VSAT = VD1 = 1V this
power loss becomes IIN(DC) (1V). "1MAX is then:
~MAX

Po

Volo

Volo

PIN

Volo +IIN(1V)

VI +1 (l+tON)
000
toFF

= - = :-:-:--:-7-:;;-;;-

VIN Is applied across L 1

~ILP-p =
Ll=

0.4 IL = 0.41 liN = 0.4 10 (

~~), therefore:

VINtoN
T(Vo - VIN)
(Vo) and since tON =
Vo
0.410 -V
IN

where: L 1 Is In henrys, f is the switching frequency in Hz

&I

3-33

Typical Applications (Continued)
To apply the above theory, a complete step-up switching
regulator is shown in Figure 20. Since VIN is 5V, VREF is tied
to VIN. The input voltage is divided by 2 to bias the error
amplifier's inverting input. The output voltage is:
VOUT = (1

+ :~)

x VINV = 2.5 X (1

circuit the inductor may saturate at turn-on because it has to
supply high peak currents to charge the output capacitor
from OV. It should also be noted that this circuit has no
supply rejection. By adding a reference voltage at the noninverting input to the error amplifier, see Figure 21, the input
voltage variations are rejected.
The LM35240 can also be used in inductorless switching
regulators. Figure 22 shows a polarity inverter which if connected to Figure 20 provides a -15V unregulated output.

+ :~)

The network 01, C1 forms a slow start circuit.
This holds the output of the error amplifier initially low thus
reducing the duty-cycle to a minimum. Without the slow start

L1

R2
12k

300~H

~2k

VO=15V

......

-.;y...

00.5"

'02
MR850

240

~345

VREf

IN914B

VIN
C"

R4
Uk
NI
5~ F

+

=:= =:=

R3
Uk

Rl
2.4k

.....
,....,

~2210
lk

CB l -

(NV

LM3524D

O.l~F=~

E"

0.1~

+

=~ 5

3k
Ry

EB

Dl

1~~4

O.~~~F

Cy

"

GND

... ,

COMP
50k

o.oOI~FT
GNO

f

5~F

CI

GND
TUH/8650-25

L1 =

> 25 turns No. 24 wire on Ferroxcube No. K300502 Torroid core.

FIGURE 20. 15V, 0.5A Step-Up Switching Regulator

100
FROM JUNCTION o.....-.±J 1-+--MI-_........_-o-15V
OF L1, 02---'
@25mA

TO NON-INVERTING
INPUT OF LM3524

-----4...-....-00GNO

GNDo---...

TL/H/8650-27

FIGURE 22
TUH/8850-28

FIGURE 21

3-34

Connection Diagram
INYINPUT

.1

U

.!!.. YREF
.!!. YIN

NIINPUT2.

+CLSENSE-

.!!. EMITTER 8
.!!. COLLECTOR B

-CL SENSE..!

.!!. COLLECTOR A

OSC OUTPUT

..l
4

...!.

.!!. EMITTER A

CT..2.

.!!!. SHUTDOWN

RT

.!.. COMPENSATION

GNO..!.

TLlH/8650-2

Top View

Order Number LM1524DJ
See NS Package Number J16A
Order Number LM2524DN or LM3524DN
See NS Package Number N16E
Order Number LM3524DM
See NS Package Number M16A

&I

3·35

r------------------------------------------------------------------,
~
~National
N

>

:::E:

.."

:l

~ Semiconductor

& LM2S7 4/LM2S74HV Series
N

:l Simple Switcher™ O.SA Step-Down Voltage Regulator
General Description

Features

The LM2574 series of regulators are monolithic integrated
circuits that provide all the active functions for a step-down
(buck) switching regulator, capable of driving a 0.5A load
with excellent line and load regulation. These devices are
available in fixed output voltages of 3.3V, 5V, 12V, 15V, and
an adjustable output version.

• 3.3V, 5V, 12V, 15V, and adjustable output versions
• Adjustable version output voltage range,
1.23V to 37V (57V for HV version) ±4% max over line
and load conditions
• Guaranteed 0.5A output current
• Wide input voltage range, 40V, up to 60V
for HV version
• Requires only 4 external components
• 52 kHz fixed frequency internal oscillator
• TIL shutdown capability, low power standby mode
• High efficiency
• Uses readily available standard inductors
• Thermal shutdown and current limit protection

Requiring a minimum number of external components,
these regulators are simple to use and include internal frequency compensation and a fixed-frequency oscillator.
The LM2574 series offers a high-efficiency replacement for
popular three-terminal linear regulators. Because of its high
efficiency, the copper traces on the printed circuit board are
normally the only heat sinking needed.
A standard series of inductors optimized for use with the
LM2574 are available from several different manufacturers.
This feature greatly simplifies the design of switch-mode
power supplies.
Other features include a guaranteed ± 4 % tolerance on output voltage within specified input voltages and output load
conditions, and ± 10% on the oscillator frequency. External
shutdown is included, featuring 50 p.A (typical) standby current. The output switch includes cycle-by-cycle current limiting, as well as thermal shutdown for full protection under
fault conditions.

Typical Application

Applications
•
•
•
•

Simple high-efficiency step-down (buck) regulator
Efficient pre-regulator for linear regulators
On-card switching regulators
Positive to negative converter (Buck-Boost)

(Fixed Output Voltage Versions)

60V Max
Unregulated -.-"'-';::-1

Regulated

L:;=:;~)f=j::;-""J~~""j~:_- Output
O.5A Load

DC Input

TL/H/11394-1

Nole: Pin numbers are for a·pln DIP package.

Connection Diagrams
14-Lead Wide
Surface Mount (WM)

a-Lead DIP (N)
FB 1 •

B •

SIOGND 2

7 OUTPUT

ON/orr 3

B •

'No Internal
connection, but
should be soldered
to PC board for
besl heat transfer.

PWRGND 4
TL/H/11394-2

Top View
B ,

Order Number LM2574-3,3HVN, LM2574HVN-5.0,
LM2574HVN-12, LM2574HVN-15, LM2574HVN-ADJ,
LM2574N-3.3, LM2574N-5.0, LM2574N-12.
LM2574N-15 or LM2574N-ADJ
See NS Package Number NOaA

TL/H/11394-3

Top View

Order Number LM2574HVM-3,3, LM2574HVM-5.0.
LM2574HVM-12, LM2574HVM-15. LM2574HVM-ADJ,
LM2574M-3,3 LM2574M-5.0, LM2574M-12,
LM2574M-15 or LM2574M-ADJ
See NS Package Number M14B

Patent Pending

3-36

r

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for avaiiability and specifications.
Maximum Supply Voltage
LM2574
LM2574HV
ON/OFF Pin Input Voltage
Output Voltage to Ground
(Steady State)

Minimum ESD Rating
(C = 100 pF, R = 1.5 kil)
Lead Temperature .
(Soldering, 10 seconds)
Maximum Junction Temperature

45V
63V
-0.3V';: V ,;: +VIN

Internally Limited

Storage Temperature Range

2kV
260'C
1500C

- 65'C to + 150'C

-40'C';: TJ';: +125'C
40V
60V

LM2S74-3.3, LM2S74HV-3.3
Electrical Characteristics Specifications with standard type face are for TJ
type apply over full Operating Temperature Range.
Symbol

Parameter

=

25'C, and those with boldface

LM2574-3.3
LM2574HV-3.3

Conditions

Limit
(Note 2)

Typ

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2

Your

Output Voltage

Your

Output Voltage
LM2574

4.75V ,;: VIN ,;: 40V, 0.1A ,;: ILOAD ,;: 0.5A

Your

Output Voltage
LM2574HV

4.75V ,;: VIN ,;: 60V, 0.1A ,;: 'LOAD';: 0.5A

'Ij

Efficiency

VIN

VIN

=

=

12V,ILOAD

12V, ILOAD

=

=

100 mA

0.5A

3.3
3.234
3.366

V
V(Min)
V(Max)

3.168/3.135
3.432/3.465

V
V(Min)
V(Max)

3.168/3.135
3.450/3.482

V(Min)
V(Max)

3.3

3.3

%

72

LM2S74-S.0, LM2S74HV-S.O
Electrical Characteristics Specifications with standard type face are for TJ
type apply over full Operating Temperature Range.
Symbol

Parameter

=

25'C, and those with boldface

LM2574-5.0
LM2574HV-5.0

Conditions
Typ

Limit
(Note 2)

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2

Your

Output Voltage

Your

Output Voltage
LM2574

7V ,;: VIN ,;: 40V, 0.1A ,;: ILOAD ,;: 0.5A

Your

Output Voltage
LM2574HV

7V,;: VIN';: 60V, 0.1A';: ILOAD';: 0.5A

'Ij

Efficiency

VIN

VIN

=

=

12V, iLOAD

12V,ILOAD

=

=

100 mA

0.5A

3-37

5
4.900
5.100

V
V(Min)
V(Max)

4.800/4.750
5.200/5.250

V
V(Min)
V(Max)

4.800/4.750
5.225/5.275

V(Min)
V(Max)

5

5

77

....

~
r

s:
N

....
U1

0l:Io

::c
<

Operating Ratings
Temperature Range
LM2574/LM2574HV
Supply Voltage
LM2574
LM2574HV

-1V

Power Dissipation

==
U1

N

%

LM2574-12, LM2574HV-12

Electrical Characteristics

Specifications with standard type face are for TJ = 25°C, and those with boldface
type apply over full Operating Temperature Range.

Symbol

Parameter

LM2574-12
LM2574HV-12

Conditions
Typ

Limit
(Note 2)

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2
Your

Your

Vour

7j

Output Voltage

VIN = 25V, ILOAD = 100 mA

s: VIN s: 40V, 0.1A s: ILOAD s: 0.5A

Output Voltage
LM2574

15V

Output Voltage
LM2574HV

15V

Efficiency

VIN = 15V, ILOAD = 0.5A

s: VIN s: SOY, 0.1 A s: ILOAD s: 0.5A

10
11.7S
12.24

V
V(Min)
V(Max)

11.52/11.40
12.48/12.80

V
V(Min)
V(Max)

11.52/11.40
12.54/12.88

V(Min)
V(Max)

12

12

88

%

LM2574-15, LM2574HV-15

Electrical Characteristics

Specifications with standard type face are for TJ = 25°C, and those with boldface
type apply over full Operating Temperature Range.

Symbol

Parameter

LM2574-15
LM2574HV-15

Conditions
Typ

Limit
(Note 2)

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2
Your

Your

Your

7j

Output Voltage

VIN = 30V, ILOAD = 100 mA

s: VIN s: 40V, 0.1A s: ILOAD s: 0.5A

Output Voltage
LM2574

18V

Output Voltage
LM2574HV

18V

Efficiency

VIN = 18V.ILOAD = 0.5A

s: VIN s: SOY, 0.1 A s: ILOAD s: 0.5A

3·38

14.70
15.30

V
V(Min)
V(Max)

14.40/14.25
15.S0/15.75

V
V(Min)
V(Max)

14.40/14.25
15.S8/15.83

V(Min)
V(Max)

15

15

15

88

%

LM2574-ADJ, LM2574HV-ADJ
Electrical Characteristics

Specifications with standard type face are for TJ = 25'C, and those with boldface
type apply over full Operating Temperature Range. Unless otherwise specified, VIN = 12V, ILOAD = 100 mAo

Symbol

Parameter

LM2574·ADJ
LM2574HV·ADJ

Conditions

Limit
(Note 2)

Typ

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2
VFB

VFB

VFB

"Ij

Feedback Voltage

1.217
1.243

V
V(Min)
V(Max)

1.193/1.180
1.267/1.280

V
V(Min)
V(Max)

1.193/1.180
1.273/1.286

V(Min)
V(Max)

1.230

VIN = 12V, ILOAD = 100 mA

Feedback Voltage
LM2574

7V ~ VIN ~ 40V, O.lA ~ ILOAD ~ 0.5A
VOUT Programmed for 5V. Circuit of Figure 2

1.230

Feedback Voltage
LM2574HV

7V ~ VIN ~ 60V, O.lA ~ ILOAD ~ 0.5A
VOUT Programmed for 5V. Circuit of Figure 2

1.230

Efficiency

VIN = 12V, VOUT = 5V, ILOAD = 0.5A

77

%

All Output Voltage Versions
Electrical Characteristics

Specifications with standard type face are for TJ = 25'C, and those with boldface
type apply over full Operating Temperature Range. Unless otherwise specified, VIN = 12V for the 3.3V, 5V, and
Adjustable version, VIN = 25V for the 12V version, and VIN = 30V for the 15V version. ILOAD = 100 mA.

Symbol

Parameter

Conditions

LM2574-XX
LM2574HV·XX

Units
(Limits)

Typ

Limit
(Note 2)
100/500

nA

47/42
58/63

kHz
kHz(Min)
kHz(Max)

1.2/1.4

V
V(max)

93

%
%(Min)

0.7/0.65
1.6/1.8

A
A(Min)
A(Max)

DEVICE PARAMETERS
Ib

Feedback Bias Current

Adjustable Version Only, VOUT = 5V

50

fo

Oscillator Frequency

(see Note 10)

52

VSAT
DC
ICL

IL

10
ISTBY
(JJA
(JJA
(JJA
(JJA

Saturation Voltage
Max Duty Cycle (ON)
Current Limit

Output Leakage Current

Quiescent Current

0.9

lOUT = 0.5A (Note 4)
(Note 5)

98

Peak Current, (Notes 4, 10)

(Notes 6, 7)

Output = OV
Output = -1V
Output = -1V

(Note 6)

1.0

30

mA(Max)
mA
mA(Max)

10

mA
mA(Max)

200

/LA
/LA(Max)

2
7.5
5

Standby Quiescent
Current

ON/OFF Pin= 5V (OFF)

Thermal Resistance

N Package, Junction to Ambient (Note 8)
N Package, Junction to Ambient (Note 9)
M Package, Junction to Ambient (Note 8)
M Package, Junction to Ambient (Note 9)

92
72
102
78

ON/OFF Pin Logic
Input Level

VOUT = OV
VOUT = Nominal Output Voltage

1.4

2.2/2.4

V(Min)

1.2

1.0/0.8

V(Max)

ON/OFF Pin Input
Current

ON/OFF Pin = 5V (OFF)

12
30

/LA
/LA(Max)

10

/LA
/LA(Max)

50

'C/W

ON/OFF CONTROL Test Circuit Figure 2
VIH
VIL
IH
IlL

ON/OFF Pin = OV (ON)

3-39

0

•

Electrical Characteristics (Continued)
Note 1: Absolu1e Maximum Ratings indicate limits beyond which damage to tha device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, bu1 do not guarantee specHic performance limits. For guaranteed specifications and test condHions, see the Electrical Characteristics.
Note 2: All limits guaranteed at room temperature (Standard type face) and at temperature extremes (bold type face). All room temperature limits are t 00%
production tested. All limits at temperature extreme. are guaranteed via correlation using standard Statistical Quality Control (SOC) methods. All limits are used
to calculate Average OutgOing QualHy Level.
Note 3: External components such as the catch diode, inductor, input and oUlput capacitors can affact switching regulator system performance. When the LM2574
is used as shown in the Figure 2 test clreu", system performance will be as shown in systam parameters section of Electrical Characteristics.
Note 4: 0u1pu1 pin sourcing current. No diode, inductor or capaCitor connected to output pin.
Note 5: Feedback pin removed from oUlpu1 and connacted to OV.
Note 6: Feedback pin removed from ou1pu1 and connected to + t 2V for the Adjustable, a.3V, and 5V versions, and + 25V for the 12V and 15V versions, to force
the output transistor OFF.
Note 7: VIN = 40V (60V for high voltage version).
Nota 8: Junction to ambient thermal resistance wHh apprOximately 1 square Inch of printed circuit board copper surrounding the leads. Additional copper area will
lower thermal resistance further. Sea application hints in this data sheet and the thermal model In SWltchers Made Simple soHware.
Note 9: Junction to ambient thermal resistance with approximately 4 square inches of 1 oz. (0.0014 in. thick) printed circuit board copper surrounding the leads.
Additional copper area will lower thermal resistance further. (Sea Note 6.)
Nota 10: The oscillator frequency reduces to approximately 18 kHz in the event of an output short or an overtoad which causes the regulated output voltage to drop
apprOximately 40% from the nominal oUlput voltage. This self protactlon feature lowers the average power dissipation of the IC by lowering the minimum dUlY cycle
from 5% down to approximately 2%.

Typical Performance Characteristics (Circuit of Figure 2)
Normalized Output Voltage
+1.0
~

I"
~

I

g

-

+0.2

-0.2
-Q.4

.....

,

~

-0.6
-1.0
-50 -25

1.2
1.0

g

0.8

~

0.6

~~

0.4

I

-0.6

25

50

75

2.0
100m~
r-- 1--1.0.0=
TJ =250 C
-:;;;:

V

I

-0.4

o

10

20

I
I

i

40

50

1.1

..... .......

....

0.9
0.8
0.7
-50 -25

'<

.5

16

i

14

B

i

25

50

75

100 125

JUNCTION TEMPERATURE (oC)

Ground PIn
TJ =125OC

1\

12

"/ ~

10

\.DAD = 500 mA

o

10

20

30

0

25

40

INPUT VOLTAGE (V)

50

'<

50

75

100 125

200
V,. =40V

.3

I"
I
5

-

ILOAD = 100 mA

o

r-

100 mA

Standby
Quiescent Current
-'. VOUT "5V
Weasured at

,

18

4
0

\.DAO
0.5

JUNCTION TEMPERATURE (oC)

20

Y,N = 25V
1..1
1.2

-+-r
=

-50 -25

60

--r-

ILDAO =500 mA

I~

1.0

~

Supply Current

1.4

1.0

30

I
I

~

1.5

INPUT VOLTAGE (V)

Current Limit

I"
I

is

I

JUNCTION TEMPERATURE (oC)

3:

.. 1

3.3~,5Vf~ADJ •

V 'f- f-" 12V t 15V
I I
I I

-0.2

100 125

~

;. 'r7-

L= 330 ~H
f\NO = 0.211

~

Io?'" I

1..0"'"

0.2

-0.6
-0

Dropout Voltage

Line Regulation
1.4

I

V,N = 20V

+0.8 I-- I.oAO =100 mA
iiI.6 I-- Normalized at
f-- TJ =:I 25 0 C
+DA I--

Iiiz

..

150

I

i""""

-

Voft/OFF" 5V
100

VIN
50

-

= 12V

I - i"""'

;!!

60

o
-50 -25

0

25

50

75

100 125

JUNCTION TEMPERATURE (OC)

TUH/t 1394-17

3-40

Typical Performance Characteristics (Circuit of Figure 2) (Continued)
Switch Saturation
Voltage

Oscillator Frequency
Normalized at 25 cC

g

~

1>
15

~

\l

~

S

t"

~

-2

l1

-6

iil

!::;

"" \.

li!
~

:

\.. Y,N =40~h

-4

~

N..K'

95

1.2

90

-8
-75 -50-25 0 25 50 75 100125150

I---

0.9

",DoC

0.8

25°C

0.7
0.6 t2 °C
0.5
0.3

~

~

!::;
0

>

~

3.0
2.5

0.1

§

"<'

15.0

~

12.5

~

7.5

.5
B

V " 1.23V
1.5 i-- our
'LOAD =100 mA
1.0

II:

ill

-50 -25

I

I

0

25

75

0.2

0.3

0.4

0.5

o

I'.....

10

20

30

40

O.IA

.........

50

60

INPUT VOLTAGE (V)

Feedback Voltage
vs Duty Cycle
20

Adjustable Version Only/

YIN = 7V ~

l..?'

10.0

I:r'

~OAO=

./

5.0

S

r-

Adjustable Version Only

15

.5
...~
~

100mA

li!

-5

1l

-10

=100 mA

~~
~ ~IN=40V

~

40V

'LOAD

"

10

ri

i

Y,N

/'

V,N =7V ......

:::::::::: ~

m -15
-20

o

100 125

r--:: ~
0.5A

~

55

o
50

0.5A

......;; t::--

60

2.5

o

- ....
......

65

Supply Current
vs Duty Cycle
17.5

2.0

0.5

70

20.0

-

1-

3.5

75 Vo-;;:5V

S
u

SWITCH CURRENT CA)

Adjustable Venlon Only

4.0

g

-~_r--

1

85 Your;. 15V
80

50

o

Minimum Operating Voltage
4.5

,...-

-

JUNCTION TEWPERATURE CDC)

5.0

-.-- - -

1.1
1.0

0.4

VIN ;; 12Y

Efficiency

1.3

20

JUNCTION TEWPERATURE CDC)

40

60

80

100

o

20

DUTY CYCLE ClI)

40

60

80

100

DUTY CYCLE ClI)
TL/H111394-4

Feedback
Pin Current
100

!

§

';' 140

50

ti-

~

~

1 1 1
.1 1 L
I 1 1

130

120

I

25

1/

100

-25

:;;!

-50

~

i!:

-75
-100
-75 -50 -25 0 25 50 75 100125150

cww)
I I

SO-14

110

J

z

~

150

Adjustable Version Only

75

B
0:

Junction to Ambient
Thermal Resistance

:x:
"- t'- 1..1

90
60

"

70
60
0

DIP-8 CN)

1 1

I

123456789

PC BOARD AREA CSQ. IN. or 1 OZ. COPPER)

JUNCTION TEWPERATURE (DC)

TL/H111394-5

3·41

>
::c
~

Typical Performance Characteristics (Circuit of Figure 2) (Continued)

II)

Continuous Mode Switching Waveforms
VOUT = SV, SOO mA Load Current, L = 330 ",H

N

....:::E
....
.......

Discontinuous Mode Switching Waveforms
VOUT = SV, 100 mA Load Current, L = 100 ",H

20V
{

10~

A

II)

20V
{
A

N

:::&
....

0.6A

B

10~

0.4A
{
B 0.2:

{ 0.4A
0.2A

o
cJ20 mV

c{20mv
AC

1.. AC

TL/H/11394-6

TL/H/11394-7

A: Output Pin Voltage, 10VIdlv
B: Inductor Current, 0.2 A/div
C: Output Ripple Voltage, 20 mV/dlv,
AC-Coupled
Horizontal Time Base: S",s/dlv

A: Output Pin Voitage,10V/div
B: Inductor Current, 0.2 A/div
C: Output Ripple Voltage, 20 mVIdiv,
AC·Coupled
Horizontal Time Base: S ",s/dlv

SOO mA Load Transient Response for Continuous
Mode Operation, L = 330 ",H, COUT = 300 ",F

2S0 mA Load Transient Response for Discontinuous
Mode Operation. L = 68 ",H, COUT = 470 ",F

50mV

A ( 50mV

AC

1..

AC

200mA
{
B 100 mA
OmA

TL/H/I1394-B

TL/H/I1394-9

A: Output Voltage, SO mY/div.
ACCoupled
B: 100 mA to 500 mA Load Pulse
Horizontal Time Base: 200 ",s/div

A: Output Voltage, SO mVIdlv.
ACCoupled
B: 50 mA to 250 mA Load Pulse
Horizontal Time Base: 200 ",s/div

Block Diagram

AI

= lk
= 1.7k
= 3.1k

3.3V. A2
5V, A2

12V, A2

=

15V, A2

= 11.3k

B.84k

For Adj. Version
AI

= Open, A2 = on

Note: Pin numbers are for the B·pin DIP package.

FIGURE 1

3-42

TLlH/I1394-10

Test Circuit and Layout Guidelines
Fixed Output Voltage Versions

CINCaurD1L1-

R1R2-

22/LF, 75V
Aluminum Electrolytic
220 /LF, 25V
Aluminum Electrolytic
Schottky, 11DQ06
330 /LH, 52627
(for 5V in, 3.3V out, use
100 /LH, RL·1284·100)
2k,0.1%
6.12k,0.1%

TLlH/11394-11

Adjustable Output Voltage Version
VOUT
R2

~ VAEF ( 1 + ~ )

~ Rl

(VOUT - 1)
VAEF

where VAEF ~ 1.23V.
R1 between 1k & Sk.

TL/H/11394-12

FIGURE 2
As in any switching regulator, layout is very important. Rap·
idly switching currents associated with wiring inductance
generate voltage transients which can cause problems. For
minimal inductance and ground loops, the length of the
leads indicated by heavy lines should be I(ept as short as
possible. Single·point grounding (as indicated) or ground
plane construction should be used for best results. When
using the Adjustable version, physically locate the program·
ming resistors near the regulator, to keep the sensitive feed·
back wiring short.

Inductor
Value
68/LH
100/LH
150/LH
220/LH
330/LH
470/LH
680/LH
1000/LH
1500/LH
2200/LH

Pulse Eng.
(Note 1)

Renco
(Note 2)

NPI
(Note 3)

52625
52626
52627
52628
52629
52631

RL·1284·68
RL·1284·100
RL·1284·150
RL·1284·220
RL·1284·330
RL·1284-470
RL·1283·680
RL·1283·1000
RL·1283·1500
RL·1283·2200

NP5915
NP5916
NP5917
NP5918/5919
NP5920/5921
NP5922
NP5923

··
•

·

FIGURE 3. Inductor Selection by
Manufacturer's Part Number

··
·

U.S. Source

European Source

Note 1: Pulse Engineering,
(619) 674·8100
P.O. Box 12236, San Diego, CA 92112

Note 3: NPII APC
+ 44 (0) 634 290588
47 Riverside, Medway City Estate
Strood, Rochester, Kent
ME24DP.
UK

Note 2: Renco Electronics Inc.,
(516) 586·5566
60 Jeffryn Blvd. East, Deer Park, NY 11729

·Contact Manufacturer

·Contact Manufacturer

3·43

•

I

LM2574 Series Buck Regulator Design Procedure
PROCEDURE (Fixed Output Voltage Versions)

EXAMPLE (Fixed Output Voltage Versions)

Given:
VOUT = Regulated Output Voltage (3.3V, 5V, 12V, or 15V)
VIN(Max) = Maximum Input Voltage
ILOAO(Max) = Maximum Load Current
1. Inductor Selection (L 1)
A. Select the correct Inductor value selection guide from
Figures 4, 5, 6 or 7. (Output voltages of 3.3V, 5V, 12V or
15V respectively). For other output voltages, see the
deSign procedure for the adjustable version.
B. From the inductor value selection guide, identify the
inductance region intersected by VIN(Max) and
ILOAO(Max).
C. Select an appropriate inductor from the table shown in
Figure 3 . Part numbers are listed for three inductor
manufacturers. The inductor chosen must be rated for
operation at the LM2574 switching frequency (52 kHz) and
for a current rating of 1.5 X ILOAO' For additional inductor
information, see the inductor section in the Application
Hints section of this data sheet.
2. Output CapaCitor Selection (COUT)
A. The value of the output capaCitor together with the
inductor defines the dominate pole-pair of the switching
regulator loop. For stable operation and an acceptable
output ripple voltage, (approximately 1% of the output
voltage) a value between 100 /loF and 470 /loF is
recommended.
B. The capacitor's voltage rating should be at least 1.5
times greater than the output voltage. For a 5V regulator,
a rating of at least BV is appropriate, and a 10V or 15V
rating is recommended.
Higher voltage electrolytic capacitors generally have lower
ESR numbers, and for this reasion it may be necessary to
select a capacitor rated for a higher voltage than would
normally be needed.
3. Catch Diode Selection (01)
A. The catch-diode current rating must be at least 1.5
times greater than the maximum load current. Also, if the
power supply design must withstand a continuous output
short, the diode should have a current rating equal to the
maximum current limit of the LM2574. The most stressful
condition for this diode is an overload or shorted output
condition.
B. The reverse voltage rating of the diode should be at
least 1.25 times the maximum input voltage.
4. Input CapaCitor (CIN)
An aluminum or tantalum electrolytic bypass capaCitor
located close to the regulator is needed for stable
operation.

Given:
VOUT = 5V
VIN(Max) = 15V
ILOAO(Max) = 0.4A
1. Inductor Selection (L 1)
A. Use the selection guide shown in Figure 5 .
B. From the selection guide, the inductance area
intersected by the 15V line and O.4A line is 330.
C. Inductor value required is 330 /loH. From the table in
Figure 3, choose Pulse Engineering PE-52627,
Renco RL-12B4-330, or NPI NP5920/5921.

2.

Output Capacitor Selection (COUT)
A. COUT = 100 /loF to 470 /loF standard aluminum
electrolytic.
B. CapaCitor voltage rating = 20V.

3.

Catch Diode Selection (01)
A. For this example, a 1A current rating is adequate.
B. Use a 20V 1N5B17 or SR102 Schottky diode, or any of
the suggested fast-recovery diodes shown in Figure 9.

4.

Input CapaCitor (CIN)
A 22 /loF aluminum electrolytic capaCitor located near the
input and ground pins provides sufficient bypassing.

3-44

r-------------------------------------------------------------------------------------~

LM2574 Series Buck Regulator Design Procedure (Continued)

~

INDUCTOR YALUE SELECTION GUIDES (For Continuous Mode Operation)

~

..,

3

60
30
20
15 680.Y\
12
10 ,.L'470 \ .......
9
~

...>~

.:

'"

:>

'"
!;i
'"

'\
330

./'

0

./
/'

/
5
0.1

~

r-

s:::

N
U'I

/
0.15

::c
<

./

./

V

I.<'"
V

.....
.Qo.

./

'"

/220\

/

r-

s:::

N

k"

150\

VV

V
~

V~

1~~

1\

0.2

0.3

0.4

0.5

MAXIMUM LOAD CURRENT (A)
TL/H/11394-26

MAXIMUM LOAD CURRENT (A)

FIGURE 4. LM2574HY·3.3Inductor Selection Guide

TLlH/11394-13

FIGURE 5. LM2574HY·5.0 Inductor Selection Guide

~

~

'"~

'"

...
...
.:

...>

:>

'"
'"X
'"

::IE
:>

::E

'"

..,to

..,

~

0

>

:>

~

::Ii

X

::Ii

MAXIMUM LOAD CURRENT (A)

MAXIMUM LOAD CURRENT (A)
TLlH/11394-14

TLlH/11394-15

FIGURE 6. LM2574HY·12 Inductor Selection Guide
250
200
150

1

!...

.

..,

100
90
80
70
60
50
40
30
20
15

\
2200..,J..

FIGURE 7. LM2574HY·15 Inductor Selection Guide

--....
--

~

rr:

,
,

~

"'-1500 ~
"'-1000-

,

- -----

,,-I-"

680

.......

470

-'

330

~

~

~

~

V

0.15

0.2

Ell

ft :< .,...

220...150

,,-~100

-

\,

,,- H'68
0.3

0.4

0.5

MAXIMUM LOAD CURRENT (A)
TL/H/11394-16

FIGURE 8. LM2574HY·ADJ Inductor Selection Guide

3-45

>

....~

.---------------------------------------------------------------------~

LM2574 Series Buck Regulator Design Procedure (Continued)

~

~

;;:

~

~

PROCEDURE (Adjustable Output Voltage Versions)

EXAMPLE (Adjustable Output Voltage Versions)

Given:
VOUT = Regulated Output Voltage
VIN(Max) = Maximum Input Voltage
ILOAO(Max) = Maximum Load Current
F = Switching Frequency (Fixed at 52 kHz)
1. Programming Output Voltage (Selecting R1 and R2, as

Given:
VOUT = 24V
VIN(Max) = 40V
ILOAO(Max) = 0.4A
F=52kHz
1. Programming Output Voltage (Selecting R1 and R2)

shown in Figure 2)

VOUT = 1.23( 1 +

Use the following formula to select the appropriate
resistor values.
VOUT = VREF (1

+ :~)

where VREF = 1.23V

:~)

Select Rl = lk

R2 = R1(VOUT -1) = lk( 24V -1)
VREF
1.23V

R1 can be between 1k and 5k. (For best temperature
coefficient and stability with time, use 1% metal film

R2 = lk (19.51 - 1) = 18.51k, closest 1% value Is 18.7k

resistors)

2.

3.

Inductor Selection (L 1)
A. Calculate the inductor Volt - microsecond constant,
E - T 0/- /Ls), from the following formula:
VOUT
1000
E - T = 0/IN - VOUT) - - - - --.--- 0/- /Ls)
VIN
F (mkHz)
B. Use the E - T value from the previous formula and
match it with the E - T number on the vertical axis of the
Inductor Value Selection Guide shown in Figure 8.
C. On the horizontal axis, select the maximum load
current.
D. Identify the inductance region intersected by the E - T
value and the maximum load current value, and note the
inductor value for that region.
E. Select an appropriate inductor from the table shown in
Figure 3. Part numbers are listed for three inductor
manufacturers. The inductor chosen must be rated for
operation at the LM2574 switching frequency (52 kHz)
and for a current rating of 1.5 x ILOAO. For additional
inductor information, see the inductor section in the
application hints section of this data sheet.

2.

Output Capacitor Selection (COUT)

3.

Inductor Selection (L1)
A. Calculate E - T 0/- /Ls)
24 1000
E - T = (40 - 24) • 40 - 52 = 185 V - /Ls
B.E-T= 185V-,...s
C. ILOAO(Max) = 0.4A
D. Inductance Region = 1000
E.lnductorValue = 1000 /LH Choose from Pul"
EngIneering Part #PE-52631, or Renco
Part #RL-1283-1000.

A. The value of the output capacitor together with the
inductor defines the dominate pole-pair of the switching
regulator loop. For stable operation, the capaCitor must
satisfy the following requirement:
VIN(Max)
COUT ~ 13,300 VOUT _ L(/LH) (/LF)

Output CapaCitor Selection (Cour)
40
A. COUT > 13,300 24 _ 1000 = 22.2 /LF
However, for acceptable outpu1 ripple voltage select
COUT ~ 100 /LF
COUT = 100 /LF electrolytic capaCitor

The above formula yields capacitor values between 5 /LF
and 1000 /LF that will satisfy the loop requirements for
stable operation. But to achieve an acceptable output
ripple voltage, (approximately 1% of the output voltage)
and transient response, the output capaCitor may need to
be several times larger than the above formula yields.
B. The capacitor's voltage rating should be at last 1.5
times greater than the output voltage. For a 24V regulator,
a rating of at least 35V is recommended.
Higher voltage electrolytiC capaCitors generally have
lower ESR numbers, and for this reasion it may be
necessary to select a capacitor rate for a higher voltage
than would normally be needed.

3-46

LM2574 Series Buck Regulator Design Procedure (Continued)
PROCEDURE (Adjustable Output Voltage Versions)

4. Catch Diode Selection (01)
A. The catch-diode current rating must be at least 1.5
times greater than the maximum load current. Also, if the
power supply design must withstand a continuous output
short, the diode should have a current rating equal to the
maximum current limit of the LM2574. The most stressful
condition for this diode is an overload or shorted output
condition. Suitable diodes are shown in the selection
guide of Figure 9.
B. The reverse voltage rating of the diode should be at
least 1.25 times the maximum input voltage.
5. Input Capacitor (CIN)
An aluminum or tantalum electrolytic bypass capacitor
located close to the regulator is needed for stable
operation.

EXAMPLE (Adjustable Output Voltage Versions)

4. Catch Diode Selection (01)
A. For this example, a 1A current rating is adequate.
B. Use a 50V MBR150 or II DQ05 Schottky diode, or any of the
suggested fast-recovery diodes in Figure 9.

5. Input Capacitor (CIN)
A 22 /LF aluminum electrolytic capacitor located near the input
and ground pins provides sufficient bypassing.

VR

1 Amp Diodes
Schottky

20V

IN5B17
SR102
MBR120P

30V

IN5B1B
SRI03
l1DQ03
MBR130P
IOJQ030

40V

IN5BI9
SRI04
l1DQ04
l1JQ04
MBR140P

50V

MBR150
SRI05
l1DQ05
IIJQ05

60V

MBR160
SRI06
l1DQ06
l1JQ06

90V

Fast Recovery

The
following
diodes
are all
rated to
100V
110FI
10JFI
MURll0
HER102

l1DQ09
FIGURE 9. Diode Selection Guide

To further simplify the buck regulator design procedure, National
Semiconductor is making available computer design software to
be used with the Simple Switcher line of switching regulators.
Sw/tchers Made Simple (version 3.3) is available on a (3!& N)
diskette for IBM compatible computers from a National
Semiconductor sales office in your area.

3-47

•

> ,----------------------------------------------------------------------,

::c
'lit

~

........

:E

t!

II)

C'I

:i

Application Hints
constant. As the load current rises or falls, the entire sawtooth current waveform also rises or falls. The average DC
value of this waveform is equal to the DC load current (in
the buck regulator configuration).
If the load current drops to a low enough level, the bottom
.of the sawtooth current waveform will reach zero, and the
switcher will change to a discontinuous mode of operation.
This is a perfectly acceptable mode of operation. Any buck
switching regulator (no matter how large the inductor value
is) will be forced to run discontinuous if the load current is
light enough.
The curve shown in Figure 10 illustrates how the peak-topeak inductor ripple current (al'NO) is allowed to change as
different maximum load currents are selected, and also how
it changes as the operating pOint varies from the upper border to the lower border within an inductance region (see
Inductor Selection guides).

INPUT CAPACITOR (C'N)
To maintain stability, the regulator input pin must be bypassed with at least a 22 p.F electrolytic capacitor. The capacitor's leads must be kept short, and located near the
regulator.
If the operating temperature range includes temperatures
below -25°C, the input capacitor value may need to be
larger. With most electrolytic capacitors, the capacitance
value decreases and the ESR increases with lower temperatures and age. Paralleling a ceramic or solid tantalum capacitor will increase the regulator stability at cold temperatures. For maximum capacitor operating lifetime, the capacitor's RMS ripple current rating should be greater than
1.2

X(~N) X

ILOAO

where ioN = VOUT for a buck regulator
T
V,N
and tON = I IViUTlv for a buck-boost regulator.
VOUT + IN
T

INDUCTOR SELECTION
All switching regulators have two basic modes of operation:
continuous and discontinuous. The difference between the
two types relates to the inductor current, whether it is flowing continuously, or if it drops to zero for a period of time in
the normal switching cycle. Each mode has distinctively different operating characteristics, which can affect the regulator performance and requirements.
The LM2574 (or any of the Simple Switcher family) can be
used for both continuous and discontinuous modes of operation.
In many cases the preferred mode of operation is in the
continuous mode. It offers better load regulation, lower peak
switch, inductor and diode currents, and can have lower output ripple voltage. But it does require relatively large inductor values to keep the inductor current flowing continuously,
especially at low output load currents.
To simplify the inductor selection process, an inductor selection guide (nomograph) was designed (see Figures 4
through 8). This guide assumes continuous mode operation, and selects an inductor that will allow a peak-to-peak
inductor ripple current (al'NO) to be a certain percentage of
the maximum design load current. In the LM2574 Simple
SWitcher, the peak-to-peak inductor ripple current percentage (of load current) is allowed to change as different design load currents are selected. By allowing the percentage
of inductor ripple current to increase for lower current applications, the inductor size and value can be kept relatively
low.

l

,nductance
Region

Q

,;


V

..s

i 40V

~

~

~

g
C>

= 200 mA

"

I

o

-SO -Z5

..........

70

2.5

o

80 5V
75

65
0.4

lA

\

15V Out

85

Supply Current
YS Duty Cycle

~

1.23V
r-- IYour
LOAD = 200 m

90

60

17.5

3.0
2.5

~-

~

20.0

Adjustable Version Only

I.....

-:-1-

--

200 rnA

SWITCH CURRENT (A)

Minimum Operating Voltage
4.0
3.5

L---I-

g
~
<3

I

JUNCTION TEMPERATURE (OC)

5.0
4.5

....

i-fo-'

25°C

0.8

0.4

-I-

-55o~

0

TJ = 25°C

95

I

~ 1.0

1;

Efficiency
100

I

Normalized at 25°C

o

20

40

60

DUTY CYCLE (lI)

80

100

Adjustable Version Only

IS

ILOAD

\.
~~

10

= 200 rnA

~ ~N-40V
VIH '7V .......

-5

~i--.

-10
-IS
-20

o

20

40

60

80

100

DUTY CYCLE (%)

TUH/11475-4

3-58

r-

is:
......
UI
.......

Typical Performance Characteristics (Circuit of Figure 2) (Continued)
Feedback Pin Current

Switching Waveforms

UI
......

100

r-

Adjustable Version Only

is:
......

75

UI

.......

50

UI

:c

25

::::
r-

J

"

-25

is:

lA

I\)

~

C.5:
[

-50
-75

UI
......

r-

is:

DC

-100
-75-50-25 0 25 50 75100125150

I\)

UI
TL/H/I147S-6

JUNCTION TEMPERATURE (OC)

VOUT ~ SV

TL/H/1147S-S

A: Output Pin Voltage. 10v/diy

.......

UI

:c
<

B: Output Pin Current, lAidiv

Load Transient Response

C: Inductor Current, O.SAldiy
D: Output Aipple Voltage, 20 mV/diy,

Output
Voltage
Change

AC·Coupled

+100mV

Horizontal Time Base: 5 "s/dlv

0
As in any switching regulator, layout is very important. Rapidly switching currents associated with wiring inductance
generate voltage transients which can cause problems. For
minimal inductance and ground loops, the length of the
leads indicated by heavy lines should be kept as short as
possible. Single-point grounding (as indicated) or ground
plane construction should be used for best results. When
using the Adjustable version, physically locate the programming resistors near the regulator, to keep the sensitive feedback wiring short.

-lOOmV

1.0A
Load
Current

O.5A

o
lOO,..sec/div.
TUH/1147S-7

Test Circuit and Layout Guidelines
Fixed Output Voltage Versions
FEEDBACK

L1

CIN -

100 "F, 75V, Aluminum Electrolytic

GoUT -

330 "F, 25V, Aluminum Electrolytic

Dl- Schottky, 110006
L1 -

330 "H, PE-S2627 (for SV in, 3.3V out,
use 100 "H, PE-921 08)

AI-2k,O.I%
TL/H/I147S-B

A2- 6.12k, 0.1%

Adjustable Output Voltage Version

VOUT
A2

~ VREF ( 1 + ~)

~ AI

(VOUT -1)
VREF

where VREF

Note: Pin numbers are for the T0-220 package.

FIGURE 2

3-59

~

1.23V, AI between lk and Sk.

II

LM2575 Series Buck Regulator Design Procedure
PROCEDURE (Fixed Output Voltage Versions)

EXAMPLE (Fixed Output Voltage Versions)

Given:
Your = Regulated Output Voltage (3.3V, 5V, 12V, or 15V)
VIN(Max) = Maximum Input Voltage
ILOAO(Max) = Maximum Load Current
1. Inductor Selection (L 1)
A. Select the correct Inductor value selection guide from
Figures 3, 4, 5, or 6. (Output voltages of 3.3V, 5V, 12V or
15V respectively). For other output voltages, see the
design procedure for the adjustable version.
B. From the inductor value selection guide, identify the
inductance region intersected by VIN(Max) and
ILOAO(Max), and note the inductor code for that region.
C. Identify the inductor value from the inductor code, and
select an appropriate inductor from the table shown in
Figure 9. Part numbers are listed for three inductor
manufacturers. The inductor chosen must be rated for
operation at the LM2575 switching frequency (52 kHz) and
for a current rating of 1.15 x ILOAO. For additional
inductor information, see the inductor section in the
Application Hints section of this data sheet.
2. Output Capacitor Selection (Cour)
A. The value of the output capacitor together with the
inductor defines the dominate pole·pair of the switching
regulator loop. For stable operation and an acceptable
output ripple voltage, (approximately 1% of the output
voltage) a value between 100 /-LF and 470 /-LF is
recommended.
B. The capacitor's voltage rating should be at least 1.5
times greater than the output voltage. For a 5V regulator,
a rating of at least SV is appropriate, and a 1OV or 15V
rating is recommended.
Higher voltage electrolytic capacitors generally have lower
ESR numbers, and for this reasion it may be necessary to
select a capacitor rated for a higher voltage than would
normally be needed.
3. Catch Diode Selection (01)
A. The catch·diode current rating must be at least 1.2
times greater than the maximum load current. Also, if the
power supply design must withstand a continuous output
short, the diode should have a current rating equal to the
maximum current limit of the LM2575. The most stressful
condition for this diode is an overload or shorted output
condition.
B. The reverse voltage rating of the diode should be at
least 1.25 times the maximum input voltage.
4. Input Capacitor (CIN)
An aluminum or tantalum electrolytic bypass capacitor
located close to the regulator is needed for stable
operation.

Given:
Your = 5V
VIN(Max) = 20V
ILOAO(Max) = O.SA
Inductor Selection (L 1)
1.
A. Use the selection guide shown in Rgure 4.
B. From the selection guide, the inductance area
intersected by the 20V line and O.SA line is L330.
C. Inductor value required is 330 /-LH. From the table in
Figure 9, choose AlE 415·0926, Pulse Engineering
PE·52627, or RL1952.

2.

Output Capacitor Selection (COUT)
A. Cour = 100 /-LF to 470 /-LF standard aluminum
electrolytic.
B. Capacitor voltage rating = 20V.

3.

Catch Diode Selection (01)
A. For this example, a 1A current rating is adequate.
B. Use a 30V 1N5S1S or SR103 Schottky diode, or any of
the suggested fast·recovery diodes shown in Figure 8.

4.

Input Capacitor (CIN)
A 47 /-LF, 25V aluminum electrolytic capacitor located near
the input and ground pins provides sufficient bypassing.

3·60

LM2575 Series Buck Regulator Design Procedure

r:i:
.....

(Continued)

....
U1

INDUCTOR VALUE SELECTION GUIDES (For Continuous Mode Operation)

U1

'-

r-

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.....
60
20
~

~

15
10

....
C>
«

....
C>

«
I-

I-

-'

~

60
40
25
20

::r:

~

r:i:

15

N
U1

...J
0

0

>

>

l-

l-

!!;

"!!;

::E

::E

=>

....

=>

=>

~

10

r:i:

=>

::E

N
U1

::E

x«

....

x

«

::E

::E

0.3

0.4

0.5 0.6

0.8

U1

0.3

1.0

TL/H/11475-11

TLlH/11475-10

FIGURE 4. LM2575(HV)-5.0

FIGURE 3. LM2575(HV)-3.3

~

~

C>

«

....

....

~ 25

>

~

I-

I-

0

=>
....
!!;

~

!!;

22

16

::E

=>

20
19

15

...x

18

::E

::E

x«

60
50
40
35
30

C>

«

~

=>

0.5 0.60.70.80.91.0

MAXIMUM LOAD CURRENT (A)

MAXIMUM LOAD CURRENT(A)

::E

0.4

::r:
<

::E

::E

0.3

0.4

0.3

O.S 0.60.70.80.91.0

0.4

0.5 0.60.70.80.91.0

MAXIMUM LOAD CURRENT (A)

MAXIMUM LOAD CURRENT (A)

TLlH/11475-13

TLlH/11475-12

FIGURE 6. LM2575(HV)-15

FIGURE 5. LM2575(HV)-12

•
0.3

0.4

O.S 0.60.70.80.91.0

MAXIMUM LOAD CURRENT (A)

FIGURE 7. LM2575(HV)-ADJ

3-61

TL/H/11475-14

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[i;

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r---------------------------------------------------------------------~

LM2575 Series Buck Regulator Design Procedure (Continued)
PROCEDURE (Adjustable Output Voltage Versions)
Given:
VOUT = Regulated Output Voltage
VIN(Max) = Maximum Input Voltage
ILOAD(Max) = Maximum Load Current
F = Switching Frequency (Fixed at 52 kHz)
1. Programming Output Voltage (Selecting R1 and R2, as
shown in Figure 2)

....
:5U)
r-.
....
:5

EXAMPLE (Adjustable Output Voltage Versions)
Given:
VOUT = 10V
VIN(Max) = 25V
ILOAO(Max) = lA
F = 52kHz
1. Programming Output Voltage (Selecting R1 and R2)

Use the following formula to select the appropriate
resistor values.
VOUT

= VREF

(1 + :~)

where VREF

VOUT = 1.23( 1

= 1.23V

R2

R1 can be between 1k and 5k. (For best temperature
coefficient and stability with time, use 1 % metal film
resistors)

U)

= Rl

+ :~)

VOUT
(-- - 1)
VREF

SelectRl = lk

= lk ( -10V
-- 1.23V

1)

R2 = lk(8.13 -1) = 7.13k,closest1% value is 7.15k

R2 = Rl (VOUT - 1 )
VREF

2.

Inductor Selection (L 1)
A. Calculate the inductor Volt e microsecond constant,
E e T (V • /Ls), from the following formula:

2.

10 1000
E· T = (25 - 10) e 25 •
= 115 V e /Ls

52

VOUT
1000
E e T = (VIN - VOUT) - - - . - . - - (V e /Ls)
VIN
F (In kHz)
B. Use the E e T value from the previous formula and
match it with the E • T number on the vertical axis of the
Inductor Value Selection Guide shown in Figure 7.
C. On the horizontal axis, select the maximum load
current.
D. Identify the inductance region intersected by the E • T
value and the maximum load current value, and note the
inductor code for that region.
E. Identify the inductor value from the inductor code, and
select an appropriate inductor from the table shown in
Figure 9. Part numbers are listed for three inductor
manufacturers. The inductor chosen must be rated for
operation at the LM2575 switching frequency (52 kHz)
and for a current rating of 1.15 x ILOAD. For additional
inductor information, see the inductor section in the
application hints section of this data sheet.
3.

Output Capacitor Selection (COUT)

Inductor Selection (L1)
A. Calculate E e T (V • /Ls)

B.EeT = 115Ve/LS
C.ILOAD(Max) = lA
D. Inductance Region = H470
E. Inductor Value = 470 /LH Choose from AlE
part #430-0634, Pulse Engineering
part #PE-53118, orRencopart #RL-1961.

3.

Output Capacitor Selection (COUT)
25
A,COUT> 7,78510.150 = 130/LF

A. The value of the output capacitor together with the
inductor defines the dominate pole-pair of the switching
regulator loop. For stable operation, the capacitor must
satisfy the following requirement:
VIN(Max)
COUT ;,: 7,785 VOUT. L(/LH) (/LF)

However, for acceptable output ripple voltage select
COUT ;,: 220 /LF
COUT = 220 /LF electrolytic capacitor

The above formula yields capacitor values between 10 /LF
and 2000 /LF that will satisfy the loop requirements for
stable operation. But to achieve an acceptable output
ripple voltage, (approximately 1 % of the output voltage)
and transient response, the output capacitor may need to
be several times larger than the above formula yields.
B. The capacitor's voltage rating should be at last 1.5
times greater than the output voltage. For a 10V regulator,
a rating of at least 15V or more is recommended.
Higher voltage electrolytic capacitors generally have
lower ESR numbers, and for this reasion it may be
necessary to select a capacitor rate for a higher voltage
than would normally be needed.

3-62

LM2575 Series Buck Regulator Design Procedure (Continued)
PROCEDURE (Adjustable Output Voltage Versions)

EXAMPLE (Adjustable Output Voltage Versions)

4. Catch Diode Selection (01)
A. The catch·diode current rating must be at least 1.2
times greater than the maximum load current. Also, if the
power supply design must withstand a continuous output
short, the diode should have a current rating equal to the
maximum current limit of the LM2575. The most stressful
condition for this diode is an overload or shorted output.
See diode selection guide in Figure 8.
B. The reverse voltage rating of the diode should be at
least 1.25 times the maximum input voltage.
5. Input CapaCitor (CIN)
An aluminum or tantalum electrolytic bypass capaCitor
located close to the regulator is needed for stable
operation.

To further simplify the buck regulator
design procedure, National Semicon·
ductor is making available computer
deSign software to be used with the
Simple Switcher line of switching regu·
lators. Swltchers Made Simple (ver·
sion 3.3) is available on a (3M H) disk·
efte for IBM compatible computers
from a National Semiconductor sales
office in your area.

VR

4. Catch Diode Selection (01)
A. For this example, a 3A current rating is adequate.
B. Use a 40V MBR340 or 31 0004 Schottky diode, or any of the
suggested fast·recovery diodes in Figure 8.

5. Input CapaCitor (CIN)
A 100 Il-F aluminum electrolytic capaCitor located near the input
and ground pins provides sufficient bypassing.

Schottky

Fast Recovery

1A

3A

20V

lN5817
MBR120P
SR102

lN5820
MBR320P
SR302

30V

lN5818
MBR130P
110003
SR103

lN5821
MBR330
310003
SR303

lN5819
MBR140P
110004
SR104

IN5822
MBR340
310004
SR304

50V

MBR150
110005
SR105

MBR350
310005
SR305

60V

MBR1601
110006
SR106

MBR3603
310006
SR306

40V

lA

3A

The following
diodes are all
rated to 100V

The following
diodes are all
rated to 1OOV

110Fl
MURll0
HER102

310Fl
MUR310
HER302

FIGURE 8. Diode Selection Guide
Inductor
Code

Inductor
Value

AlE
(Note 1)

Pulse Eng.
(Note 2)

Renco
(Note 3)

UOO

lOOIl-H

415·0930

PE·92108

RL2444

U50

150 Il-H

415·0953

PE·53113

RU954

L220

22Oll-H

415·0922

PE·52626

RL1953

L330

33Oll-H

415·0926

PE·52627

RL1952
RL1951

L470

47Oll-H

415·0927

PE·53114

L680

68Oll-H

415·0928

PE·52629

RL1950

H150

150 Il-H

415·0936

PE·53115

RL2445

H220

22Oll-H

430·0636

PE·53116

RL2446

H330

33Oll-H

430·0635

PE·53117

RL2447

H470

47Oll-H

430·0634

PE·53118

RU961

H680

68Oll-H

415·0935

PE·53119

RL1960

Hl000

1000 Il-H

415·0934

PE·53120

RL1959

H1500

1500 Il-H

415·0933

PE·53121

RL1958

H2200

2200 Il-H

415·0945

PE·53122

RL2448

Notal: AlE MagnetiCS. div. Vernatron Corp .• Passive Components Group. (813) 347·2181. 2801
Note 2: Pulse Engineering, (619) 674-8100, P.O. Box 12236, San Diego, CA 92112.
Note 3: Renco Electronics Inc .. (516) 586·5566, 60 Jeffryn Blvd. East, Deer Park, NY 11729.

72nd Street North. St Petersburg. Fl33710.

FIGURE 9. Inductor Selection by Manufacturer's Part Number

3·63

•

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an
.....
an
C'I

:s
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Ie
an
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:s
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an
.....
an

....
::i....
an
.....
....an
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r---------------------------------------------------------------------~

Application Hints
pensive, the bobbin core type, consists of wire wrapped on
a ferrite rod core. This type of construction makes for an
inexpensive inductor, but since the magnetiC flux is not completely contained within the core, it generates more electromagnetic interference (EM I). This EMI can cause problems
in sensitive circuits, or can give incorrect scope readings
because of induced voltages in the scope probe .

INPUT CAPACITOR (CIN)
To maintain stability, the regulator input pin must be bypassed with at least a 47 /-LF electrolytic capacitor. The capacitor's leads must be kept short, and located near the
regulator.
If the operating temperature range includes temperatures
below -25°C, the input capacitor value may need to be
larger. With most electrolytic capacitors, the capacitance
value decreases and the ESR increases with lower temperatures and age. Paralleling a ceramic or solid tantalum capacitor will increase the regulator stability at cold temperatures. For maximum capacitor operating lifetime, the capacitor's RMS ripple current rating should be greater than

1.2

x

C~N)

The inductors listed in the selection chart include ferrite pot
core construction for AI E, powdered iron toroid for Pulse
Engineering, and ferrite bobbin core for Renco .
An inductor should not be operated beyond its maximum
rated current because it may saturate. When an inductor
begins to saturate, the inductance decreases rapidly and
the inductor begins to look mainly resistive (the DC resistance of the winding). This will cause the switch current to
rise very rapidly. Different inductor types have different saturation characteristics, and this should be kept in mind when
selecting an inductor.
The inductor manufacturer's data sheets include current
and energy limits to avoid inductor saturation.

X ILOAD

where tON = VOUT for a buck regulator
VIN
T
and toTN = Iv IV,uTl v for a buck-boost regulator.
OUT + IN

INDUCTOR RIPPLE CURRENT

When the switcher is operating in the continuous mode, the
inductor current waveform ranges from a triangular to a
sawtooth type of waveform (depending on the input voltage). For a given input voltage and output voltage, the peakto-peak amplitude of this inductor current waveform remains
constant. As the load current rises or falls, the entire sawtooth current waveform also rises or falls. The average DC
value of this waveform is equal to the DC load current (in
the buck regulator configuration).
If the load current drops to a low enough level, the bottom
of the sawtooth current waveform will reach zero, and the
switcher will change to a discontinuous mode of operation.
This is a perfectly acceptable mode of operation. Any buck
switching regulator (no matter how large the inductor value
is) will be forced to run discontinuous if the load current is
light enough.

INDUCTOR SELECTION

All switching regulators have two basic modes of operation:
continuous and discontinuous. The difference between the
two types relates to the inductor current, whether it is flowing continuously, or if it drops to zero for a period of time in
the normal switching cycle. Each mode has distinctively different operating characteristics, which can affect the regulator performance and requirements.
The LM2575 (or any of the Simple Switcher family) can be
used for both continuous and discontinuous modes of operation.
The inductor value selection guides in Figures 3 through 7
were designed for buck regulator designs of the continuous
inductor current type. When using inductor values shown in
the inductor selection guide, the peak-to-peak inductor ripple current will be approximately 20% to 30% of the maximum DC current. With relatively heavy load currents, the
circuit operates in the continuous mode (inductor current
always flowing), but under light load conditions, the circuit
will be forced to the discontinuous mode (inductor current
falls to zero for a period of time). This discontinuous mode
of operation is perfectly acceptable. For light loads (less
than approximately 200 mAl it may be desirable to operate
the regulator in the discontinuous mode, primarily because
of the lower inductor values required for the discontinuous
mode.

OUTPUT CAPACITOR

An output capacitor is required to filter the output voltage
and is needed for loop stability. The capacitor should be
located near the LM2575 using short pc board traces. Standard aluminum electrolytics are usually adequate, but low
ESR types are recommended for low output ripple voltage
and good stability. The ESR of a capacitor depends on
many factors, some which are: the value, the voltage rating,
physical size and the type of construction. In general, low
value or low voltage (less than 12V) electrolytic capaCitors
usually have higher ESR numbers.

The selection guide chooses inductor values suitable for
continuous mode operation, but if the inductor value chosen
is prohibitively high, the designer should investigate the possibility of discontinuous operation. The computer design
software Swltchers Made Simple will provide all component values for discontinuous (as well as continuous) mode
of operation.

The amount of output ripple voltage is primarily a function of
the ESR (Equivalent Series Resistance) of the output capacitor and the amplitude of the inductor ripple current
(b.lIND)' See the section on inductor ripple current in Application Hints.
The lower capaCitor values (220 /-LF-680 /-LF) will allow typically 50 mV to 150 mV of output ripple voltage, while largervalue capacitors will reduce the ripple to approximately
20 mV to 50 mY.

Inductors are available in different styles such as pot core,
toriod, E-frame, bobbin core, etc., as well as different core
materials, such as ferrites and powdered iron. The least ex-

Output Ripple Voltage = (aIIND) (ESR of COUT)

3-64

.-----------------------------------------------------------------------------'r
s::
.....
CI1

Application Hints (Continued)
To further reduce the output ripple voltage, several standard
electrolytic capacitors may be paralleled, or a higher-grade
capacitor may be used. Such capacitors are often called
"high-frequency," "low-inductance," or "Iow-ESR." These
will reduce the output ripple to 10 mV or 20 mY. However,
when operating in the continuous mode, reducing the ESR
below 0.050 can cause instability in the regulator.
Tantalum capacitors can have a very low ESR, and should
be carefully evaluated if it is the only output capacitor. Because of their good low temperature characteristics, a tantalum can be used in parallel with aluminum electrolytics, with
the tantalum making up 10% or 20% of the total capacitance.

FEEDBACK CONNECTION

The LM2575 (fixed voltage versions) feedbacl< pin must be
wired to the output voltage point of the switching power
supply. When using the adjustable version, physically locate
both output voltage programming resistors near the LM2575
to avoid picking up unwanted noise. Avoid using resistors
greater than 100 kO because of the increased chance of
noise pickup.
ON/OFF INPUT

For normal operation, the ON/OFF pin should be grounded
or driven with a low-level TTL voltage (typically below 1.6V).
To put the regulator into standby mode, drive this pin with a
high-level TTL or CMOS Signal. The ON/OFF pin can be
safely pulled up to + VIN without a resistor in series with it.
The ON/OFF pin should not be left open.

The capacitor's ripple current rating at 52 kHz should be at
least 50% higher than the peak-to-peak inductor ripple current.

GROUNDING

CATCH DIODE
Buck regulators require a diode to provide a return path for
the inductor current when the switch is off. This diode
should be located close to the LM2575 using short leads
and short printed circuit traces.
Because of their fast switching speed and low forward voltage drop, Schottky diodes provide the best efficiency, especially in low output voltage switching regulators (less than
5V). Fast-Recovery, High-Efficiency, or Ultra-Fast Recovery
diodes are also suitable, but some types with an abrupt turnoff characteristic may cause instability and EMI problems. A
fast-recovery diode with soft recovery characteristics is a
better choice. Standard 60 Hz diodes (e.g., 1N4001 or
1N5400, etc.) are also not suItable. See Figure 8 for
Schottky and "soft" fast-recovery diode selection guide.

......
CI1
......
r

s::
.....
CI1
......
CI1

::E:

:::r
s::

N
CI1

......
CI1
"r

s::
N
CI1
......
CI1

::E:

<

To maintain output voltage stability, the power ground connections must be low-impedance (see Figure 2). For the
TO-S style package, the case is ground. For the 5-lead
TO-220 style package, both the tab and pin S are ground
and either connection may be used, as they are both part of
the same copper lead frame.
With the N or M packages, all the pins labeled ground, power ground, or signal ground should be soldered directly to
wide printed circuit board copper traces. This assures both
low inductance connections and good thermal properties.
HEAT SINK/THERMAL CONSIDERATIONS
In many cases, no heat sink is required to keep the LM2575
junction temperature within the allowed operating range. For
each application, to determine whether or not a het sink will
be required, the following must be identified:
1. Maximum ambient temperature (in the application).

OUTPUT VOLTAGE RIPPLE AND TRANSIENTS
The output voltage of a switching power supply will contain
a sawtooth ripple voltage at the switcher frequency, typically
about 1 % of the output voltage, and may also contain short
voltage spikes at the peaks of the sawtooth waveform.
The output ripple voltage is due mainly to the inductor sawtooth ripple current multiplied by the ESR of the output capacitor. (See the inductor selection in the application hints.)

2. Maximum regulator power dissipation (in application).
S. Maximum allowed junction temperature (150'C for the
LM1575 or 125'C for the LM2575). For a safe, conservative design, a temperature approximately 15'C cooler
than the maximum temperature should be selected.
4. LM2575 package thermal resistances OJA and 0JC.

The voltage spikes are present because of the the fast
switching action of the output switch, and the parasitic inductance of the output filter capacitor. To minimize these
voltage spikes, special low inductance capacitors can be
used, and their lead lengths must be kept short. Wiring inductance, stray capacitance, as well as the scope probe
used to evaluate these transients, all contribute to the amplitude of these spikes.

Total power dissipated by the LM2575 can be estimated as
follows:
Po = (VIN) (10) + (VO/VIN) (ILOAD) (VSAT)
where 10 (quiescent current) and VSAT can be found in the
Characteristic Curves shown previously, VIN is the applied
minimum input voltage, Vo is the regulated output voltage,
and ILOAD is the load current. The dynamic losses during
turn-on and turn-off are negligible if a Schottky type catch
diode is used.

An additional small LC filter (20 /LH & 100 /LF) can be added
to the output (as shown in Figure 15) to further reduce the
amount of output ripple and transients. A 10 x reduction in
output ripple voltage and transients is possible with this filter.

S-65

&I

>

::c
II)
~

II)

N

~
U;
t;
N

::!
....I

:>
::c
II)

t;

.-

:e
....I
U;
~

II)
.-

::!
....I

r---------------------------------------------------------------------~

Application Hints (Continued)
When no heat sink is used, the junction temperature rise
can be determined by the following:

Additional Applications
INVERTING REGULATOR
Figure 10 shows a LM2575-12 in a buck-boost configuration

6.TJ = (Po) (6JAl
To arrive at the actual operating junction temperature, add
the junction temperature rise to the maximum ambient temperature.

to generate a negative 12V output from a positive input voltage. This circuit bootstraps the regulator's ground pin to the
negative output voltage, then by grounding the feedback
pin, the regulator senses the inverted output voltage and
regulates it to -12V.

TJ = 6.TJ + TA
If the actual operating junction temperature is greater than
the selected safe operating junction temperature determined in step 3, then a heat sink is required.
When using a heat sink, the junction temperature rise can
be determined by the following:

For an input voltage of 12V or more, the maximum available
output current in this configuration is approximately 0.35A.
At lighter loads, the minimum input voltage required drops to
apprOximately 4.7V.
The switch currents in this buck-boost configuration are
higher than in the standard buck-mode design, thus lowering the available output current. Also, the start-up input current of the buck-boost converter is higher than the standard
buck-mode regulator, and this may overload an input power
source with a current limit less than 1.5A. Using a delayed
turn-on or an undervoltage lockout circuit (described in the
next section) would allow the input voltage to rise to a high
enough level before the switcher would be allowed to turn
on.
Because of the structural differences between the buck and
the buck-boost regulator topologies, the buck regulator design procedure section can not be used to to select the
inductor or the output capacitor. The recommended range
of inductor values for the buck-boost design is between
68 pH and 220 p.H, and the output capacitor values must be
larger than what is normally required for buck designs. Low
input voltages or high output currents require a large value
output capaCitor (in the thousands of micro Farads).

6.TJ = (Po) (6JC + 6interface + 6Heatslnkl
The operating junction temperature will be:
TJ = TA + 6.TJ
As above, if the actual operating junction temperature is
greater than the selected safe operating junction temperature, then a larger heat sink is required (one that has a lower
thermal resistance).
When using the LM2575 in the plastic DIP (N) or surface
mount (M) packages, several items about the thermal properties of the packages should be understood. The majority
of the heat is conducted out of the package through the
leads, with a minor portion through the plastic parts of the
package. Since the lead frame is solid copper, heat from the
die is readily conducted through the leads to the printed
circuit board copper, which is acting as a heat sink.
For best thermal performance, the ground pins and all the
unconnected pins should be soldered to generous amounts
of printed circuit board copper, such as a ground plane.
Large areas of copper provide the best transfer of heat to
the surrounding air. Copper on both sides of the board is
also helpful in getting the heat away from the package, even
if there is no direct copper contact between the two sides.
Thermal resistance numbers as low as 40·C/W for the SO
package, and 30"C/W for the N package can be realized
with a carefully engineered pc board.
Included on the Swltchers Made SImple design software is
a more precise (non-linear) thermal model that can be used
to determine junction temperature with different input-output
parameters or different component values. It can also calculate the heat sink themnal resistance required to maintain
the regulators junction temperature below the maximum operating temperature.

+12 TO +25V
UNREGULATED
DC INPUT

I :::: ILOAO (YIN + IVol) + VIN Ivol X _ 1 _
P
VIN
VIN + Ivol
2 L1 fosc
Where fosc = 52 kHz. Under normal continuous inductor
current operating conditions, the minimum VIN represents
the worst case. Select an inductor that is rated for the peak
current antiCipated.
Also, the maximum voltage appearing across the regulator
is the absolute sum of the input and output voltage. For a
-12V output, the maximum input voltage for the LM2575 is
+ 28V, or + 48V for the LM2575HV.
The Swltchers Made Simple (version 3.3) deSign software
can be used to detemnine the feasibility of regulator designs
using different topologies, different input-output parameters,
different components, etc.

fEEDBACK
+VIN

!l C1N

I

The peak inductor current, which is the same as the peak
switch current, can be calculated from the following formula:

LN2575HV-12

4
OUTPUT

L1

1

100 }'H

l00}'f L3....- - - -.. 2
GND
5 'ON/Off

C:-;~Dl

-.j~ lN5819

+

-~

T

toUT

2200 }'f

-12V @0.35A
REGULATED
OUTPUT

FIGURE 10. Inverting Buck·Boost Develops -12V
3-66

TUH/11475-15

....~

Additional Applications (Continued)

U"I

NEGATIVE BOOST REGULATOR

+VIN

Another variation on the buck-boost topology is the negative boost configuration. The circuit in Figure 11 accepts an
input voltage ranging from - 5V to -12V and provides a
regulated -12V output. Input voltages greater than -12V
will cause the output to rise above -12V, but will not damage the regulator.

+VIN

--"'"+--9---9-:'-1, LM2575 - XX
+

......
U"I
::c
~
r-

s::

N

U"I

......
r-

~
TL/H/11475-17

Note: Pin numbers are for the TO·220 package.

FIGURE 12_ Undervoltage Lockout for Buck Circuit

+VIN

+VIN

. . . ; ; . ; .. . . . . . .-

. . . . .- -. . . .;;;.1,

+

LM2575 - XX
3

Gnd

150 )'H
Typical Load Current
-S.2V
500 mA for V,N ~ - 7V

-12V

200mAforV'N~

TUH/11475-16

Note: Pin numbers are for TO-220 package.

FIGURE 11_ Negative Boost

-Your

UNDERVOLTAGELOCKOUT

TL/H/1147S-18

In some applications it is desirable to keep the regulator off
until the input voltage reaches a certain threshold. An undervoltage lockout circuit which accomplishes this task is
shown in Figure 12, while Figure 13 shows the same circuit
applied to a buck-boost configuration. These circuits keep
the regulator off until the input voltage reaches a predetermined level.
VTH :::: VZl

Note: Complete circuit not shown (see Figure 1(}J.
Note: Pin numbers are for the T0-220 package.

FIGURE 13. Undervoltage Lockout
for Buck·Boost Circuit

+VIN
+VIN
"';;';'--4I~--1....--::-:-t,

+ 2VSE (Q1)

LM2575 - XX

DELAYED STARTUP

The ON/OFF pin can be used to provide a delayed startup
feature as shown in Figure 14. With an input voltage of 20V
and for the part values shown, the circuit provides approximately 10 ms of delay time before the circuit begins switching. Increasing the RC time constant can provide longer delay times. But excessively large RC time constants can
cause problems with input voltages that are high in 60 Hz or
120 Hz ripple, by coupling the ripple into the ON/OFF pin.

47k

TL/H/1147S-19

Note: Complete circuit not shown.
Note: Pin numbers are for the TO-220 package.

ADJUSTABLE OUTPUT, LOW·RIPPLE
POWER SUPPLY

FIGURE 14. Delayed Startup

A 1A power supply that features an adjustable output volt·
age is shown in Figure 15. An additional L-C filter that reduces the output ripple by a factor of 10 or more is included in
this circuit.

3-67

s::
N

~
::c

Note: Complete circuit not shown.

to

s::
....

U"I

Because of the boosting function of this type of regulator,
the switch current is relatively high, especially at low input
voltages. Output load current limitations are a result of the
maximum current rating of the switch. Also, boost regulators
can not provide current limiting load protection in the event
of a shorted load, so some other means (such as a fuse)
may be necessary.

-5

......
r-

~

<

>.----------------------------------------------------------------------.

:c
II)

rn

Additional Applications (Continued)
FEEDBACK

C'I

:!!
..J

it;

.....

60V

+VIN

r------"
L2
I

4

......---tLM2575HV-ADJ

UNREGULATED DC INPUT

OUTPUT

I

L1

~P----II-""'-R-2-~

II)

C'I

:!!

+

:>

1'' '

..J

:c
II)

.....

...

II)

:!!

..J
....

COUT

I
I

50k

...
:!!
II)

..J

@lA

1""1

- _ _ 01I
10 _ _ _ _

optional output ripple lilter

II)

.....

OUTPUT
VOLTAGE

.......,....--1~+-1.2 to 55V

TLlH/I1475-20

Note: Pin numbers are lor the T0-220 package.

FIGURE 15. 1.2V to 55V Adjustable 1A Power Supply with Low Output Ripple

Definition of Terms

EQUIVALENT SERIES INDUCTANCE (ESL)
The pure inductance component of a capacitor (see Figure
16). The amount of Inductance is determined to a large
extent on the capacitor's construction. In a buck regulator,
this unwanted inductance causes voltage spikes to appear
on the output.

BUCK REGULATOR
A switching regulator topology in which a higher voltage is
converted to a lower voltage. Also known as a step-down
switching regulator.
BUCK-BOOST REGULATOR
A switching regulator topology in which a positive voltage is
converted to a negative voltage without a transformer.

OUTPUT RIPPLE VOLTAGE
The AC component of the switching regulator's output voltage. It is usually dominated by the output capacitor's ESR
multiplied by the inductor's ripple current (b.IINO)' The peakto-peak value of this sawtooth ripple current can be determined by reading the Inductor Ripple Current section of the
Application hints.

DUTY CYCLE (D)
Ratio of the output switch's on-time to the oscillator period.

for buck regulator

for buck-boost regulator

D = toN = VOUT

T
D = tON =

T

CAPACITOR RIPPLE CURRENT
RMS value of the maximum allowable alternating current at
which a capacitor can be operated continuously at a specified temperature.

VIN

Ivol
Ivol + VIN

STANDBY QUIESCENT CURRENT (ISTBY)
Supply current required by the LM2575 when in the standby
mode (Olil/OFF pin is driven to TIL-high voltage, thus turning the output switch OFF).

CATCH DIODE OR CURRENT STEERING DIODE
The diode which provides a return path for the load current
when the LM2575 switch is OFF.
EFFICIENCY (7/)
The proportion of input power actually delivered to the load.
POUT

7/

INDUCTOR RIPPLE CURRENT (b.IINO)
The peak-to-peak value of the inductor current waveform,
typically a sawtooth waveform when the regulator is operating in the continuous mode (vs. discontinuous mode).

POUT

= PiN = POUT + PLOSS

CAPACITOR EQUIVALENT SERIES RESISTANCE (ESR)
The purely resistive component of a real capaCitor's impedance (see Figure 16). It causes power loss resulting in capacitor heating, which directly affects the capacitor's operating lifetime. When used as a switching regulator output
filter, higher ESR values result in higher output ripple voltages.

CONTINUOUS/DISCONTINUOUS MODE OPERATION
Relates to the inductor current. In the continuous mode, the
inductor current is always flowing and never drops to zero,
vs. the discontinuous mode, where the inductor current
drops to zero for a period of time in the normal switching
cycle.
INDUCTOR SATURATION
The condition which exists when an inductor cannot hold
any more magnetic flux. When an inductor saturates, the
inductor appears less inductive and the resistive component
dominates. Inductor current is then limited only by the DC
resistance of the wire and the available source current.

-~-~'\..-I}TL/H/11475-21

FIGURE 16. Simple Model of a Real CapaCitor
Most standard aluminum electrolytic capacitors in the
100 ",F-1000 ",F range have 0.50 to 0.10 ESR. Highergrade capacitors ("Iow-ESR", "high-frequency", or "low-inductance"') in the 100 ",F -1000 ",F range generally have
ESR of less than 0.150.

OPERATING VOLT MICROSECOND CONSTANT (EeTop)
The product (in Volte",s) of the voltage applied to the inductor and the time the voltage is applied. This EeTop constant
is a measure of the energy handling capability of an inductor
and is dependent upon the type of core, the core area, the
number of turns, and the duty cycle.

3-68

,-----------------------------------------------------------------------------, r
3:
.....
Connection Diagrams
en
(XX indicates output voltage option. See ordering information table for complete part number.)
en
......
r
Straight Leads
Bent, Staggered Leads
3:
5-Lead TO-220 (T)
5-Lead TO-220 m
.....
en
4- Feedback
en
Feedback
:t:
3- Ground
3-Ground

....

0 J

1

i'-"I""

i't--"'I""

1

2- Output
l-VIN

....

:::r

2-0utput
l-VIN
TL/H/11475-22

TLiH/11475-23

Top View
LM2575T-XX or LM2575HVT-XX
See NS Package Number T05A

_

/C....Pin.l.3 &: 5

~PinS2&:4

N

TLiH/11475-24

Side View
LM2575T-XX Flow LB03 or LM2575HVT-XX Flow LB03
See NS Package Number T05D
16-Lead DIP (N)

•

24-Lead Sur1ace Mount (M)
16 V,
15 ,IN

PWR GND

23

2

22

OUTPUT

21

4

20

GND

19

FB

18

FB
ON/OFF
TLiH/11475-25

"No Internal Connection

OUTPUT

SIG GND

OUTPUT

ON/OFF

VIN
VIN

Top View
PWR GND

LM2575N-XX or LM2575HVN-XX
See NS Package Number N16A

TL/H/11475-26

·No Internal Connection

Top View
LM2575M-XX or LM2575HVM-XX
See NS Package Number M24B
4-Lead TO-3 (K)

+VIN

OUTPUT

FEEDBACK

ON/OFF

TLiH/11475-27

Bottom View
LM1575K-XX or LM1575HVK-XX/883
See NS Package Number K04A

3-69

3:
N
en
en
.......
r
3:

....

Top View

~

:t:

<

Ordering Information
Package
Type

NSC
Package
Number

Standard
Voltage Rating
(40V)

High
Voltage Rating
(60V)

5·Lead TO·220
Straight Leads

T05A

LM2575T·3.3
LM2575T·5.0
LM2575T·12
LM2575T·15
LM2575T·ADJ

LM2575HVT·3.3
LM2575HVT·5.0
LM2575HVT·12
LM2575HVT·15
LM2575HVT·ADJ

5·Lead TO·220
Bent and
Staggered Leads

T05D

LM2575T·3.3 Flow LB03
LM2575T·5.0 Flow LB03
LM2575T·12 Flow LB03
LM2575T·15 Flow LB03
LM2575T·ADJ Flow LB03

LM2575HVT·3.3 Flow LB03
LM2575HVT·5.0 Flow LB03
LM2575HVT·12 Flow LB03
LM2575HVT·15 Flow LB03
LM2575HVT·ADJ Flow LB03

16·Pin Molded
DIP

N16A

LM2575N·5.0
LM2575N·12
LM2575N·15
LM2575N·ADJ

LM2575HVN·5.0
LM2575HVN·12
LM2575HVN·15
LM2575HVN·ADJ

24·Pin
Surface Mount

M24B

LM2575M·5.0
LM2575M·12
LM2575M·15
LM2575M·ADJ

LM2575HVM·5.0
LM2575HVM·12
LM2575HVM·15
LM2575HVM·ADJ

4·PinTO·3

K04A

LM1575K·3.3/883
LM1575K·5.0/883
LM1575K·12/883
LM1575K·15/883
LM1575K·ADJ/883

LM 1575HVK·3.3/883
LM 1575HVK·5.0/883
LM1575HVK·12/883
LM1575HVK·15/883
LM1575HVK·ADJ/883

3·70

Temperature
Range

-40·C

S;

TJ

S;

+125·C

-55·C

S;

TJ

S;

+ 1500C

'?A National
~ Semiconductor

LM2576/LM2576HV Series
Simple Switcher™ 3A Step-Down Voltage Regulator
General Description

Features

The LM2576 series of regulators are monolithic integrated
circuits that provide all the active functions for a step-down
(buck) switching regulator, capable of driving 3A load with
excellent line and load regulation. These devices are available in fixed output voltages of 3.3V, 5V, 12V, 15V, and an
adjustable output version.

• 3.3V,5V, 12V, 15V, and adjustable output versions
• Adjustable version output voltage range,
1.23V to 37V (57V for HV version) ±4% max over
line and load conditions
• Guaranteed 3A output current
• Wide input voltage range, 40V up to 60V for
HV version
• Requires only 4 extemal components
• 52 kHz fixed frequency internal oscillator
• TTL shutdown capability, low power standby mode
• High efficiency
• Uses readily available standard inductors
• Thermal shutdown and current limit protection
• P+ Product Enhancement tested

Requiring a minimum number of external components,
these regulators are simple to use and include internal frequency compensation and a fixed-frequency oscillator.
The LM2576 series offers a high-efficiency replacement for
popular three-terminal linear regulators. It substantially reduces the size of the heat sink, and in some cases no heat
sink is required.
A standard series of inductors optimzed for use with the
LM2576 are available from several different manufacturers.
This feature greatly simplifies the design of switch-mode
power supplies.
Other features include a guaranteed ± 4% tolerance on output voltage within specified input voltages and output load
conditions, and ± 10% on the oscillator frequency. External
shutdown is included, featuring 50 /LA (typical) standby current. The output switch includes cycle-by-cycle current limiting, as well as thremal shutdown for full protection under
fault conditions.

Typical Application

Applications
•
•
•
•

Simple high-efficiency step-down (buck) regulator
Efficient pre-regulator for linear regulators
On-card switching regulators
Positive to negative converter (Buck-Boost)

(Fixed Output Voltage Versions)
r-;:;;;;;;"l~FE~EO~BA~C!.K

7V - 40V
(GOV for HV)

Lt.42576/

+V'N

UNR~U~:~~-_-~,

I

4

__--,
L1

LM2576HV-

:::ULATED

L~;5~.O~~~1r,~~:t:-OUTPUT
'OO

i~o "F

-=

r

D1

J

pH +

lN5822

<:OUT

3" lOAD

1000 I'F

TL/H/11476-1

FIGURE 1

•

Block Diagram
UNR~~U~;ij~"""_-1JJ-_ _ _ _-I

3.3V R2 = 1.7k
5V, R2 = 3.1k
12V, R2 = 8.84k
15V, R2 = 11.3k
For ADJ. Version
Rl = Open, R2 = 011

TLlH/11476-2

Patent Pending

3-71

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Maximum Supply Voltage
LM2576
45V
LM2576HV
63V
(5N/OFF Pin Input Voltage
-0.3V s; V S; + VIN
Output Voltage to Ground
-1V
(Steady State)
Power Dissipation
Internally Limited
Storage Temperature Range

Minimum ESD Rating
(C = 100 pF, R = 1.5 k!l)
Lead Temperature
(Soldering, 10 Seconds)
Maximum Junction Temperature

260'C
150'C

Operating Ratings
Temperature Range
LM2576/LM2576HV

-40'C s; TJ s;

+ 125'C

Supply Voltage
LM2576
LM2576HV

+ 150'C

- 65'C to

2kV

40V
60V

LM2576-3.3, LM2576HV-3.3
Electrical Characteristics Specifications with standard type face are for TJ = 25'C, and those with boldface
type apply over full Operating Temperature Range.

Symbol

Parameter

LM2576-3.3
LM2576HV-3.3

Conditions
Typ

Limit
(Note 2)

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2
VOUT

VOUT

VOUT

T/

Output Voltage

VIN = 12V. ILOAD
Circuit of Figure 2

=

Output Voltage
LM2576

6V S; VIN ,;; 40V.0.5A
Circuit of Figure 2

S;

Output Voltage
LM2576HV

6V S; VIN ,;; 60V, 0.5A
Circuit of Figure 2

S;

Efficiency

VIN

=

12V, ILOAD

3.3

0.5A

3.234
3.366

V
V(Min)
V(Max)

3.168/3.135
3.432/3.465

V
V(Min)
V(Max)

3.168/3.135
3.450/3.482

V
V(Min)
V(Max)

3.3

ILOAD ,;; 3A

3.3

ILOAD ,;; 3A

= 3A

75

%

LM2576-5.0, LM2576HV-5.0
Electrical Characteristics Specifications with standard type face are for TJ = 25'C. and those with boldface
type apply over full Operating Temperature Range.

Symbol

Parameter

LM2576-5.0
LM2576HV-5.0

Conditions
Typ

Umit
(Note 2)

Units
(Umits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2
VOUT

VOUT

VOUT

T/

Output Voltage

VIN = 12V, ILOAD
Circuit of Figure 2

=

0.5A

5.0

Output Voltage
LM2576

0.5A';; ILOAD';; 3A,
8V S; VIN S; 40V
Circuit of Rgure 2

5.0

Output Voltage
LM2576HV

0.5A S; ILOAD ,;; SA,
8V ,;; VIN S; 60V
Circuit of Figure 2

5.0

Efficiency

VIN

=

12V. ILOAD

=

SA

S·72

77

4.900
5.100

V
V(Min)
V(Max)

4.800/4.750
5.200/5.250

V
V(Min)
V(Max)

4.800/4.750
5.225/5.275

V
V(Min)
V(Max)
%

LM2576-12, LM2576HV-12

Electrical Characteristics Specifications with standard type face are for TJ = 25°C, and those with boldface
type apply over full Operating Temperature Range.

Symbol

Parameter

LM2576·12
LM2576HV·12

Conditions

Limit
(Note 2)

Typ

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2

Your
Your
Your
'71

Output Voltage

VIN = 25V, ILOAD
Circuit of Figure 2

=

t2

0.5A

Output Voltage
LM2576

0.5A ,,; ILOAD ,,; 3A,
15V,,; VIN ,,; 40V
Circuit of Figure 2

12

Output Voltage
LM2576HV

0.5A ,,; ILOAD ,,; 3A,
15V,,; VIN ,,; 60V
Circuit of Figure 2

12

Efficiency

VIN

=

15V,ILOAD

=

t1.76
12.24

V
V(Min)
V(Max)

11.52/11.40
12.48/12.60

V
V(Min)
V(Max)

11.52/11.40
12.54/12.66

V
V(Min)
V(Max)

%

88

3A

LM2576-15, LM2576HV-15

Electrical Characteristics Specifications with standard type face are for TJ = 25°C, and those with boldface
type apply over full Operating Temperature Range.

Symbol

Parameter

LM2576-15
LM2576HV·15

Conditions

Limit
(Note 2)

Typ

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2

Your

Output Voltage

VIN = 25V, ILOAD
Circuit of A'gure 2

=

Your

Output Voltage
LM2576

0.5A ,,; ILOAD ,,; 3A,
18V,,; VIN ,,; 40V
Circuit of Figure 2

15

Your

Output Voltage
LM2576HV

0.5A ,,; ILOAD ,,; 3A,
18V,,; VIN ,,; 60V
Circuit of Figure 2

15

'71

Efficiency

VIN

=

18V, ILOAD

=

14.70
t5.30

V
V(Min)
V(Max)

14.40/14.25
15.60/15.75

V
V(Min)
V(Max)

14.40/14.25
15.68/15.83

V
V(Min)
V(Max)

15

0.5A

%

88

3A

LM2576-ADJ, LM2576HV·ADJ

Electrical Characteristics Specifications with standard type face are for TJ = 25°C, and those with boldface
type apply over full Operating Temperature Range.

Symbol

LM2576·ADJ
LM2576HV·ADJ

Conditions

Parameter

Typ

Limit
(Note 2)

Units
(Limits)

SYSTEM PARAMETERS (Note 3) Test Circuit Figure 2

Your

Feedback Voltage

= 12V,ILOAD =
Your = 5V,
VIN

1.230

0.5A

Circuit of Figure 2

Your

Feedback Voltage
LM2576

O.5A ,,; ILOAD ,,; 3A,
8V,,; VIN"; 40V
Your = 5V, Circuit of Figure 2

1.230

Your

Feedback Voltage
LM2576HV

0.5A ,,; ILOAD ,,; 3A,
8V,,; VIN"; 60V
Your = 5V, Circuit of Figure 2

1.230

'71

Efficiency

VIN = 12V,ILOAD = 3A,

Your

3·73

1.217
1.243

V
V(Min)
V(Max)

1.193/1.180
1.267/1.280

V
V(Min)
V(Max)

1.193/1.180
1.273/1.286
= 5V

77

V
V(Min)
V(Max)

%

•

All Output Voltage Versions
Electrical Characteristics Specifications with standard type face are for TJ = 25·C, and those with boldface
= 12V for the 3.3V,
= 500 mAo

type apply over full Operating Temperature Range. Unless otherwise specified, VIN
version, VIN

Symbol

=

=

25V for the 12V version, and VIN

30V for the 15V version. ILOAD

Parameter

5V, and Adjustable

LM2576·XX
LM2576HV·XX

Conditions

Units
(Umits)

Typ

Limit
(Note 2)

50

100/500

nA

47/42
58/63

kHz
kHz (Min)
kHz (Max)

1.8/2.0

V
V(Max)

93

%
%(Min)

4.2/3.5
6.9/7.5

A
A(Min)
A(Max)

DEVICE PARAMETERS

=

Ib

Feedback Bias Current

VOUT

fo

Oscillator Frequency

(Note 10)

VSAT

DC
ICL

IL

10
ISTBY
OJA
OJA
OJC

Saturation Voltage
Max Duty Cycle (ON)
Current Limit

Output Leakage Current

Quiescent Current

lOUT

=

5V (Adjustable Version Only)

52

1.4

3A (Note 4)

98

(Note 5)
(Notes 4 and 10)

5.8

Output = OV
Output = -1V
Output = -1V

(Notes 6 and 7)

(Note 6)

2
30

mA(Max)
mA
mA(Max)

10

mA
mA(Max)

200

/LA
/LA(Max)

7.5
5

=

Standby Quiescent
Current

ON/OFF Pin

5V (OFF)

Thermal Resistance

T Package, Junction to Ambient (Note 8)
T Package, Junction to Ambient (Note 9)
T Package, Junction to Case

50
65
45
2

·C/W

ONIOFF CONTROL Test Circuit Figure 2
VIH
VIL
IIH
IlL

=
=

Oiii/OFFPin
LogiC Input Level

VOUT

ON/OFF Pin Input
Current

ON/OFF Pin

VOUT

OV

1.4

2.2/2.4

V(Min)

Nominal Output Voltage

1.2

1.0/0.8

V(Max)

30

/LA
/LA(Max)

10

/LA
/LA(Max)

ON/OFF Pin

=
=

5V (OFF)
OV (ON)

12
0

Nole 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate cendHions for which the device is
intended to be functional. but do not guarantee specific performance limits. For guaranteed specifications and test conditions. see the Electrical Characteristics.
Note 2: All limits guaranteed at room temperature (standard type face) and at temperature extremes (bold type lace). All room temperature limits are 100%
production tested. All limits at tempsratura extreme. are guaranteed via cerrelation using standard Statistical Quality Control (SaC) methods.
Note 3: Extema! cemponents such as tha catch dloda. inductor. input and output capacHers can affect switching regulator system performance. When the
LM2576/LM2576HV Is used as shown in the F/{/uf9 2 test circuit. system performance will be as shown In system parameters section of Electrical Characteristics.
Note 4: Output pin sourcing current. No diode, Inductor or capacitor connected to output.
Note 5: Feedback pin removed from output and cennected to OV.
Note 6: Feedback pin removed from output and cennected to + 12V for the Adjustable. 3.3V. and 5V versions. and + 25V for the 12V and 15V versions. to force
the output transistor OFF.
Note 7: VIN = 40V (BOV for high voltage version).
Note 8: Junction to ambient thermal resistance (no external heat sink) for the 5 lead TO·220 package mounted vertically. with V. inch leads in a socket. or on a PC
board with minimum cepper area.
Note 9: Junction to ambient thermal resistance (no extemal heat sink) for the 5 lead TO-220 packsge mounted vertically. withY. inch leads soldered to a PC board
containing approximately 4 square inches of copper area surrounding the leads.
Note 10: The oscillator frequency reduces to approximately II kHz in the event of an output short or an overload which causes the regulated output voltage to drop
approximately 40% from the nominal output voltage. This self protection feature lowers the average power dissipation of the IC by lowering the minimum duty cycle
from 5% down to approximately 2%.

3-74

r

s::
N

Typical Performance Characteristics (Circuit of Figure 2)

U1

.....
Q)

.......
r
Normalized Output Voltage
+1.0

g +0.6 -+0.4 -

!

Normalized at
I-- TJ = 25°C

~

~

5

-

+0.2

i,.;-"

~

~

g

~OAD = 500 rnA

~

~

-0.2

'"

,.

-0.4

-0.6

~

0.8

~

0.4

~

~

~

'cOAD = 500 rnLTJ 25°C

=

1.0

~

0

r-

-0.2

I

-0.4

25

50

75

100 125

10

20

".

........

~

 ,----------------------------------------------------------------------,
%

Je

Typical Performance Characteristics (Circuit of Figur9 2) (Continued)

:5....'"

Feedback Pin Current

It)

Switching Waveforms

AeO:

100

~
'"
:::IE
....I

Adjustable Version Only

!....

...z

'"::>'"u
z

ii:

'"u...

......
II>

0

75

4A

50

B

25

II

0

f2A
l 0

~

r

-25

4A

-50

Ct2A

-75

D (

-100
-75 -50 -25 0

0

25 50 75 100125150

5,..s/dlv
TL/H/11476-6

JUNCTION TEMPERATURE (DC)
VOUT

TL/11476-4

= ISV

A: Output Pin Voltage, 50Vldiv

Load Transient Response

B: Inductor Current, 0.2 Aldiv
C: Inductor Current, 2A1dlv

Output

+ 100 mV

Voltage

0

Change

0: Output Ripple Voltage, SO mVldiv,
AC·Coupled

Horizontal Time Base: 5 "s/dlv

-100mV

As in any switching regulator, layout is very important. Rap·
idly switching currents associated with wiring inductance
generate voltage transients which can cause problems. For
minimal inductance and ground loops, the length of the
leads indicated by heavy lines should be kept as short as
possible. Single-point grounding (as indicated) or ground
plane construction should be used for best results. When
using the Adjustable version, physically locate the programming resistors near the regulator, to keep the sensitive
feedback wiring short.

3A

Load
Current

2A
lA

o
100,..s/div
TUH/11476-5

Test Circuit and Layout Guidelines
Fixed Output Voltage Versions
FEEDBACK
CIN-100

LM2576HV-

"F, 7SV, Aluminum ElectrolytiC

COUT- 1000

FIXED OUTPUT

,..F, 25V, Aluminum Electrolytic

01 - Schottky, MBR3eO

3

Ll- 100 "H, Pulse Eng. PE·9210B

'ON/OFF

RI- 2k,0.1%
R2- 6.12k, 0.1%
TL/H/11476-7

Adjustable Output Voltage Version
FEEDBACK

LM2576HV-

3 'ON/OFF

4

VOUT

Ll

ADJ
5

= VREF ( 1 + ~ )

R2 = Rl (VOUT - 1)
VREF

+ CaUT
1000 }'F

where VREF

TL/H/11476-6

FIGURE 2

3-76

= 1.23V, Rl between 1k and Sk.

LM2576 Series Buck Regulator Design Procedure
PROCEDURE (Fixed Output Voltage Versions)

EXAMPLE (Fixed Output Voltage Versions)

Given:
VOUT = Regulated Output Voltage (3.3V, 5V, 12V, or 15V)
VIN(Max) = Maximum Input Voltage
ILOAD(Max) = Maximum Load Current
Inductor Selection (L1)
1.
A. Select the correct Inductor value selection guide from
Figures 3, 4, 5, or 6 . (Output voltages of 3.3V, 5V, 12V or
15V respectively). For other output voltages, see the
design procedure for the adjustable version.
B. From the inductor value selection guide, identify the
inductance region intersected by VIN(Max) and
ILOAD(Max), and note the inductor code for that region.
C. Identify the inductor value from the inductor code, and
select an appropriate inductor from the table shown in
Figure 3 . Part numbers are listed for three inductor
manufacturers. The inductor chosen must be rated for
operation at the LM2576 switching frequency (52 kHz) and
for a current rating of 1.15 x ILOAD. For additional
inductor information, see the inductor section in the
Application Hints section of this data sheet.
2. Output Capacitor Selection (COUT)
A. The value of the output capacitor together with the
inductor defines the dominate pole-pair of the switching
regulator loop. For stable operation and an acceptable
output ripple voltage, (approximately 1% of the output
voltage) a value between 100 j.LF and 470 j.LF is
recommended.
B. The capacitor's voltage rating should be at least 1.5
times greater than the output voltage. For a 5V regulator,
a rating of at least 8V is appropriate, and a 10V or 15V
rating is recommended.
Higher voltage electrolytic capacitors generally have lower
ESR numbers, and for this reason it may be necessary to
select a capacitor rated for a higher voltage than would
normally be needed.
3. Catch Diode Selection (01)
A. The catch-diode current rating must be at least 1.2
times greater than the maximum load current. Also, if the
power supply design must withstand a continuous output
short, the diode should have a current rating equal to the
maximum current limit of the LM2576. The most stressful
condition for this diode is an overload or shorted output
condition.
B. The reverse voltage rating of the diode should be at
least 1.25 times the maximum input voltage.
4. Input CapaCitor (CIN)
An aluminum or tantalum electrolytic bypass capacitor
located close to the regulator is needed for stable
operation.

Given:
VOUT = 5V
VIN(Max) = 15V
ILOAD(Max) = 3A
Inductor Selection (L 1)
1.
A. Use the selection guide shown in Figure 4 .
B. From the selection guide, the inductance area
intersected by the 15V line and 3A line is L100.
C. Inductor value required is 100 j.LH. From the table in
Figure 3. Choose AlE 415·0930, Pulse Engineering
PE92108, or Renco RL2444.

2.

Output Capacitor Selection (COUT)
A. COUT = 680 j.LF to 2000 j.LF standard aluminum
electrolytic.
B. Capacitor voltage rating = 20V.

3.

Catch Diode Selection (01)
A. For this example, a 3A current rating is adequate.
B. Use a 20V 1N5823 or SR302 Schottky diode, or any of
the suggested fast-recovery diodes shown in Figure 8 .

4.

Input CapaCitor (CIN)
A 100 j.LF, 25V aluminum electrolytic capacitor located
near the input and ground pins provides sufficient
bypassing.

3-77

•

LM2576 Series Buck Regulator Design Procedure (Continued)
INDUCTOR VALUE SELECTION GUIDES (For Continuous Mode Operation)

~
w

~
!:;

g
....
::>

60
40
20
15
10
8

"-

a5

'"
"<><
::>

"

MAXIMUM LOAD CURRENT (Al
TLlH/11476-10

TLlH/11476-9

FIGURE 4. LM2576(HV)-5.0

FIGURE 3. LM2576(HV)-3.3
60

~
w

'"<

!:;

g
....

20
18

~

a5

~

,.'"~

16
15

.4

.5.6.7.8

1.0

1.5

2.0

.4

2.5 3.0

.5.6.7.8

1.0

1.5

2.0

2.5 3.0

MAXIMUM LOAD CURRENT (Al

MAXIMUM LOAD CURRENT (Al

TL/H/11476-12

TLlH/11476-11

FIGURE 6. LM2576(HV)-15

FIGURE 5. LM2576(HV)-12

0.4

0.5 0.6 0.70.8 1.0
1.5
MAXIMUM LOAD CURRENT CA)
FIGURE 7. LM2576(HV)-ADJ

3·78

2.0

2.5 3.0
TLlH/11476-13

LM2576 Series Buck Regulator Design Procedure (Continued)
PROCEDURE (Adjustable Output Voltage Versions)

EXAMPLE (Adjustable Output Voltage Versions)

Given:
VOUT = Regulated Output Voltage
VIN(Max) = Maximum Input Voltage
ILOAO(Max) = Maximum Load Current
F = Switching Frequency (Fixed at 52 kHz)
1.
Programming Output Voltage (Selecting R1 and R2, as
shown in Figure 2)

Given:
VOUT = 10V
VIN(Max) = 25V
ILOAD(Max) = 3A
F = 52 kHz
1.
Programming Output Voltage (Selecting R1 and R2)

Use the following formula to select the appropriate
resistor values.
VOUT = VREF ( 1

+ :~)

VOUT = 1.23( 1

R2 = 1k (8.13 - 1) = 7.13k, closest 1% value is 7.15k

2.

Inductor Selection (L 1)
A. Calculate the inductor Volt • microsecond constant,
E • T (V • p.s), from the following formula:

Inductor Selection (L 1)
A. Calculate E • T (V • p.s)
10 1000
E - T = (25 - 10) • 25 = 115 V • p.s

52

VOUT
1000
E. T = (VIN - VOUT) - - . - . - - (V 0 p.s)
VIN
F(mkHz)
B. Use the E - T value from the previous formula and
match it with the E • T number on the vertical axis of the
Inductor Value Selection Guide shown in Figure 7.
C. On the horizontal axis, select the maximum load
current.
D. Identify the inductance region intersected by the E • T
value and the maximum load current value, and note the
inductor code for that region.
E. Identify the inductor value from the inductor code, and
select an appropriate inductor from the table shown in
Figure 9. Part numbers are listed for three inductor
manufacturers. The inductor chosen must be rated for
operation at the LM2576 switching frequency (52 kHz)
and for a current rating of 1.15 x ILOAD. For additional
inductor information, see the inductor section in the
application hints section of this data sheet.

3.

Select R1 = 1k

R2=R1(VOUT_1)=1k(10V -1)
VREF
1.23V

where VREF = 1.23V

R1 can be between 1k and 5k. (For best temperature
coefficient and stability with time, use 1% metal film
resistors)

2.

+ :~)

B.E·T= 115V.p.s
C.ILOAO(Max) = 3A
D.lnductance Region = H150
E. Inductor Value = 150 p.H Choose from AlE
part #415·0936 Pulse EngIneerIng
part # PE·531115, or Renco part #RL2445.

3.

Output Capacitor Selection (COUT)

Output Capacitor Selection (COUT)
25

A. The value of the output capacitor together with the
inductor defines the dominate pole·pair of the switching
regulator loop. For stable operation, the capacitor must
satisfy the following requirement:
VIN(Max)
COUT ~ 13,300 V
L( H (p.F)
OUT- p.)

A. COUT

> 13,300 10 • 150 = 22.2 p.F

However, for acceptable output ripple voltage select
COUT ~ 680 p.F
COUT = 680 p.F electroly1ic capacitor

The above formula yields capacitor values between 10 p.F
and 2200 p.F that will satisfy the loop requirements for
stable operation. But to achieve an acceptable output
ripple voltage, (approximately 1 % of the output voltage)
and transient response, the output capacitor may need to
be several times larger than the above formula yields.
B. The capacitor's voltage rating should be at last 1.5
times greater than the output voltage. For a 10V regulator,
a rating of at least 15V or more is recommended.
Higher voltage electroly1ic capacitors generally have
lower ESR numbers, and for this reason it may be
necessary to select a capacitor rate for a higher voltage
than would normally be needed.

3·79

LM2576 Series Buck Regulator Design Procedure (Continued)
PROCEDURE (Adjustable Output Voltage Versions)

EXAMPLE (Adjustable Output Voltage Versions)

4. Catch Diode Selection (01)
A. The catch-diode current rating must be at least 1.2
times greater than the maximum load current. Also, if the
power supply design must withstand a continuous output
short, the diode should have a current rating equal to the
maximum current limit of the LM2576. The most stressful
condition for this diode is an overload or shorted output.
See diode selection guide in Figure 8 .
B. The reverse voltage rating of the diode should be at
least 1.25 times the maximum input voltage.
5. Input Capacitor (CIN)
An aluminum or tantalum electrolytic bypass capacitor
located close to the regulator is needed for stable
operation.
Schottky

VR

3A

5. Input Capacitor (CIN)
A 100 /LF aluminum electrolytic capacitor located near the input
and ground pins provides sufficient bypassing.

Fast Recovery

4A-6A

20V

lN5820
MBR320P
SR302

lN5B23

30V

lN5821
MBR330
310003
SR303

50W003
lN5B24

lN5B22
MBR340
310004
SR304

MBR340
50W004
lN5825

50V

MBR350
310005
SR305

50W005

60V

MBR360
0006
SR306

50WR06
50S0060

40V

4. Catch Diode Selection (01)
A. For this example, a 3.3A current rating is adequate.
B. Use a 30V 310003 Schottky diode, or any of the suggested
fast-recovery diodes in Figure 8.

3A

4A-6A

The following
diodes are all
rated to 100V

The following
diodes are all
rated to 1OOV

50WF10
MUR410
HER602

31DF1
HER302

To further simplify the buck regulator
design procedure, National Semiconductor is making available computer
design software to be used with the
Simple Switcher line of switching regulators. Switchers Made Simple (Version 3.3) is available on a (3~") diskette for IBM compatible computers
from a National Semiconductor sales
office in your area.

FIGURE 8. Diode Selection Guide
Inductor
Code

Inductor
Value

AlE
(Note 1)

Pulse Eng.
(Note 2)

Renco
(Note 3)

L47

47/LH

415-0932

PE-53112

RL2442

L68

68/LH

415-0931

PE-92114

RL2443

Ll00

100/LH

415-0930

PE-92108

RL2444

L150

150/LH

415-0953

PE-53113

RL1954

L220

220/LH

415-0922

PE-52626

RL1953

L330

330/LH

415-0926

PE-52627

RL1952

L470

470/LH

415-0927

PE-53114

RL1951

L680

6BO /LH

415-0928

PE-52629

RL1950

H150

150/LH

415-0936

PE-53115

RL2445

H220

220/LH

430-0636

PE-53116

RL2446

H330

330/LH

430-0635

PE-53117

RL2447

H470

470/LH

430-0634

PE-53118

RL1961

H680

680/LH

415-0935

PE-53119

RL1960

Hl000

1000/LH

415-0934

PE-53120

RL 1959

H1500

1500/LH

415-0933

PE-53121

RL1958

H2200

2200/LH

415-0945

PE-53122

RL2448

Note 1: AlE Magnetics Division. Vernatron Corporation. Passive Components GrouP. (813) 347-2181. 2801 72nd Street North. St Petersburg, FL 33710.
Note 2: Pu..... Engineering. (619) 674-8100. P.O. Box 12235. San Diego. CA 92112.
Note 3: Renco Electronics Incorporated. (516) 586-5566. 60 Jeffryn Blvd. East. Deer Park. NY 11729.

FIGURE 9. Inductor Selection by Manufacturer's Part Number
3-80

r-----------------------------------------------------------------------------,
Application Hints

N

INPUT CAPACITOR (CIN)

Inductors are available in different styles such as pot core,
toriod, E-frame, bobbin core, etc., as well as different core
materials, such as ferrites and powdered iron. The least expensive, the bobbin core type, consists of wire wrapped on
a ferrite rod core. This type of construction makes for an
inexpensive inductor, but since the magnetic flux is not completely contained within the core, it generates more electromagnetic interference (EMI). This EMI can cause problems
in sensitive circuits, or can give incorrect scope readings
because of induced voltages in the scope probe.
The inductors listed in the selection chart include ferrite pot
core construction for AlE, powdered iron toroid for Pulse
Engineering, and ferrite bobbin core for Renco.

To maintain stability, the regulator input pin must be bypassed with at least a 100 ",F electrolytic capacitor. The
capacitor's leads must be kept short, and located near the
regulator.
If the operating temperature range includes temperatures
below - 25'C, the input capacitor value may need to be
larger. With most electrolytic capacitors, the capacitance
value decreases and the ESR increases with lower temperatures and age. Paralleling a ceramic or solid tantalum capacitor will increase the regulator stability at cold temperatures. For maximum capacitor operating lifetime, the capacitor's RMS ripple current rating should be greater than
1.2

x

where

r
3:

An inductor should not be operated beyond its maximum
rated current because it may saturate. When an inductor
begins to saturate, the inductance decreases rapidly and
the inductor begins to look mainly resistive (the DC resistance of the winding). This will cause the switch current to
rise very rapidly. Different inductor types have different saturation characteristics, and this should be kept in mind when
selecting an inductor.

T

( tON) X ILOAO

t~N = V~~T for a buck regulator

and toTN = Iv IV,uTl v for a buck-boost regulator.
OUT + IN

The inductor manufacturer's data sheets include current
and energy limits to avoid inductor saturation.

INDUCTOR SELECTION

INDUCTOR RIPPLE CURRENT

All switching regulators have two basic modes of operation:
continuous and discontinuous. The difference between the
two types relates to the inductor current, whether it is flowing continuously, or if it drops to zero for a period of time in
the normal switching cycle. Each mode has distinctively different operating characteristics, which can affect the regulator performance and requirements.
The LM2576 (or any of the Simple Switcher family) can be
used for both continuous and discontinuous modes of operation.
The inductor value selection guides in Figure 3 through Figure 7 were designed for buck regulator designs of the continuous inductor current type. When using inductor values
shown in the inductor selection guide, the peak-to-peak inductor ripple current will be approximately 20% to 30% of
the maximum DC current. With relatively heavy load currents, the circuit operates in the continuous mode (inductor
current always flowing), but under light load conditions, the
circuit will be forced to the discontinuous mode (inductor
current falls to zero for a period of time). This discontinuous
mode of operation is perfectly acceptable. For light loads
(less than approximately 300 mAl it may be desirable to
operate the regulator in the discontinuous mode, primarily
because of the lower inductor values required for the discontinuous mode.
The selection guide chooses inductor values suitable for
continuous mode operation, but if the inductor value chosen
is prohibitively high, the designer should investigate the possibility of discontinuous operation. The computer design
software Swltchers Made Simple will provide all component values for discontinuous (as well as continuous) mode
of operation.

When the switcher is operating in the continuous mode, the
inductor current waveform ranges from a triangular to a
sawtooth type of waveform (depending on the input voltage). For a given input voltage and output voltage, the peakto-peak amplitude of this inductor current waveform remains
constant. As the load current rises or falls, the entire sawtooth current waveform also rises or falls. The average DC
value of this waveform is equal to the DC load current (in
the buck regulator configuration).
If the load current drops to a low enough level, the bottom
of the sawtooth current waveform will reach zero, and the
switcher will change to a discontinuous mode of operation.
This is a perfectly acceptable mode of operation. Any buck
switching regulator (no matter how large the inductor value
is) will be forced to run discontinuous if the load current is
light enough.

OUTPUT CAPACITOR
An output capacitor is required to filter the output voltage
and is needed for loop stability. The capacitor should be
located near the LM2576 using short pc board traces. Standard aluminum electrolytics are usually adequate, but low
ESR types are recommended for low output ripple voltage
and good stability. The ESR of a capacitor depends on
many factors, some which are: the value, the voltage rating,
physical size and the type of construction. In general, low
value or low voltage (less than 12V) electrolytic capacitors
usually have higher ESR numbers.
The amount of output ripple voltage is primarily a function of
the ESR (Equivalent Series Resistance) of the output capaCitor and the amplitude of the inductor ripple current
(aIINO). See the section on inductor ripple current in Application Hints.
The lower capacitor values (220 ",F-1000 ",F) will allow
typically 50 mV to 150 mV of output ripple voltage, while
larger-value capacitors will reduce the ripple to approximately 20 mV to 50 mY.
Output Ripple Voltage = (aIINO) (ESR of COUT)

3-81

~
.....
r
3:

N
U'I

d:
::::c
<

>

::J:
CD

"""

&I)

N

:E
..J

......
~

&I)

N

:E
..J

r-----------------------------------------------------------------------,
Application Hints (Continued)
To further reduce the output ripple voltage, several standard
electrolytic capacitors may be paralleled, or a higher-grade
capacitor may be used. Such capacitors are often called
"high-frequency," "low-inductance," or "Iow-ESR." These
will reduce the output ripple to 10 mV or 20 mY. However,
when operating in the continuous mode, reducing the ESR
below 0.03.11 can cause instability in the regulator.

ON/OFF INPUT
For normal operation, the ON/OFF pin should be grounded
or driven with a low-level TTL voltage (typically below 1.6V).
To put the regulator into standby mode, drive this pin with a
high-level TTL or CMOS signal. The ON/OFF pin can be
safely pulled up to + VIN without a resistor in series with it.
The ON/OFF pin should not be left open .

Tantalum capacitors can have a very low ESR, and should
be carefully evaluated if it is the only output capacitor. Because of their good low temperature characteristics, a tantalum can be used in parallel with aluminum electrolytics, with
the tantalum making up 10% or 20% of the total capacitance.

GROUNDING
To maintain output voltage stability, the power ground connections must be low-impedance (see Figure 2). For the
5-lead TO-220 style package, both the tab and pin 3 are
ground and either connection may be used, as they are both
part of the same copper lead frame.

The capacitor's ripple current rating at 52 kHz should be at
least 50% higher than the peak-to-peak inductor ripple current.

HEAT SINK/THERMAL CONSIDERATIONS
In many cases, only a small heat sink is required to keep the
LM2576 junction temperature within the allowed operating
range. For each application, to determine whether or not a
heat sink will be required, the following must be identified:
1. Maximum ambient temperature (in the application).

CATCH DIODE
Buck regulators require a diode to provide a return path for
the inductor current when the switch is off. This diode
should be located close to the LM2576 using short leads
and short printed circuit traces.
Because of their fast switching speed and low forward voltage drop, Schottky diodes provide the best efficiency, especially in low output voltage switching regulators (less than
5V). Fast-Recovery, High-Efficiency, or Ultra-Fast Recovery
diodes are also suitable, but some types with an abrupt turnoff characteristic may cause instability and EMI problems. A
fast-recovery diode with soft recovery characteristics is a
better choice. Standard 60 Hz diodes (e.g., 1N4001 or
1N5400, etc.) are also not suitable. See Figure 8 for
Schottky and "soft" fast-recovery diode selection guide.

2. Maximum regulator power dissipation (in application).
3. Maximum allowed junction temperature (125°C for the
LM2576). For a safe, conservative deSign, a temperature
approximately 15°C cooler than the maximum temperatures should be selected.
4. LM2576 package thermal resistances 8JA and 8JC.
Total power diSSipated by the LM2576 can be estimated as
follows:
Po = (VIN)(IQ) + (VoIVIN)(lLOAO)(VSAT)
where IQ (quiescent current) and VSAT can be found in the
Characteristic Curves shown previously, VIN is the applied
minimum input voltage, Vo is the regulated output voltage,
and ILOAO is the load current. The dynamiC losses during
turn-on and turn-off are negligible if a Schottky type catch
diode is used.

OUTPUT VOLTAGE RIPPLE AND TRANSIENTS
The output voltage of a switching power supply will contain
a sawtooth ripple voltage at the switcher frequency, typically
about 1% of the output voltage, and may also contain short
voltage spikes at the peaks of the sawtooth waveform.

When no heat sink is used, the junction temperature rise
can be determined by the following:

The output ripple voltage is due mainly to the inductor sawtooth ripple current multiplied by the ESR of the output capacitor. (See the inductor selection in the application hints.)
The voltage spikes are present because of the the fast
switching action of the output switch, and the parasitic inductance of the output filter capaCitor. To minimize these
voltage spikes, special low inductance capaCitors can be
used, and their lead lengths must be kept short. Wiring inductance, stray capaCitance, as well as the scope probe
used to evaluate these transients, all contribute to the amplitude of these spikes.

ATJ = (PO)(8JA)
To arrive at the actual operating junction temperature, add
the junction temperature rise to the maximum ambient temperature.
TJ=ATJ+TA
If the actual operating junction temperature is greater than
the selected safe operating junction temperature determined in step 3, then a heat sink is required.
When using a heat sink, the junction temperature rise can
be determined by the following:

An additional small LC filter (20 ,..H & 100 ,..F) can be added
to the output (as shown in Figure 15) to further reduce the
amount of output ripple and transients. A 10 X reduction in
output ripple voltage and transients is possible with this filter.

ATJ = (Po) (lIJC + lIinterface + lIHeatsiniJ
The operating junction temperature will be:
TJ = TA + ATJ
As above, if the actual operating junction temperature is
greater than the selected safe operating junction temperature, then a larger heat sink is required (one that has a lower
thermal resistance).
Included on the Switcher Made Simple design software is
a more precise (non-linear) thermal model that can be used
to determine junction temperature with different input-output
parameters or different component values. It can also calculate the heat sink thermal resistance required to maintain
the regulators junction temperature below the maximum operating temperature.

FEEDBACK CONNECTION
The LM2576 (fixed voltage versions) feedback pin must be
wired to the output voltage pOint of the switching power
supply. When using the adjustable version, physically locate
both output voltage programming resistors near the LM2576
to avoid picking up unwanted noise. Avoid using resistors
greater than 100 k.n because of the increased chance of
noise pickup.

3-82

Additional Applications
INVERTING REGULATOR

NEGATIVE BOOST REGULATOR
Another variation on the buck-boost topology is the negative boost configuration. The circuit in Figure 11 accepts an
input voltage ranging from -5V to -12V and provides a
regulated -12V output. Input voltages greater than -12V
will cause the output to rise above -12V, but will not damage the regulator.

Figure 10 shows a LM2576-12 in a buck-boost configuration
to generate a negative 12V output from a positive input voltage. This circuit bootstraps the regulator's ground pin to the
negative output voltage, then by grounding the feedback
pin, the regulator senses the inverted output voltage and
regulates it to -12V.

For an input voltage of 12V or more, the maximum available
output current in this configuration is approximately 700 mA.
At lighter loads, the minimum input voltage required drops to
approximately 4.7V.
The switch currents in this buck-boost configuration are
higher than in the standard buck-mode design, thus lowering the available output current. Also, the start-up input current of the buck-boost converter is higher than the standard
buck-mode regulator, and this may overload an input power
source with a current limit less than 0.6A. Using a delayed
turn-on or an undervoltage lockout circuit (described in the
next section) would allow the input voltage to rise to a high
enough level before the switcher would be allowed to turn
on.
Because of the structural differences between the buck and
the buck-boost regulator topologies, the buck regulator design procedure section can not be used to to select the
inductor or the output capacitor. The recommended range
of inductor values for the buck-boost design is between
68 ""H and 220 ""H, and the output capacitor values must be
larger than what is normally required for buck deSigns. Low
input voltages or high output currents require a large value
output capacitor (in the thousands of micro Farads).
The peak inductor current, which is the same as the peak
switch current, can be calculated from the following formula:

Typical Load Current

100 pH

400 mA for V,N = - 5.2V
750 mA for Y,N = -7V

-5 to -12V
Note: Heat sink may be required.

TLlH/11476-15

FIGURE 11. Negative Boost
Because of the boosting function of this type of regulator,
the switch current is relatively high, especially at low input
voltages. Output load current limitations are a result of the
maximum current rating of the switch. Also, boost regulators
can not provide current limiting load protection in the event
of a shorted load, so some other means (such as a fuse)
may be necessary.
UNDERVOLTAGELOCKOUT
In some applications it is desirable to keep the regulator off
until the input voltage reaches a certain threshold. An undervoltage lockout circuit which accomplishes this task is
shown in Figure 12, while Figure 13 shows the same circuit
applied to a buck-boost configuration. These circuits keep
the regulator off until the input voltage reaches a predetermined level.

_ ILOAD (VIN + IVol)
VIN Ivol
1
+---X--P
VIN
VIN + Ivol
2Ll fose
Where fose = 52 kHz. Under normal continuous inductor
current operating conditions, the minimum VIN represents
the worst case. Select an inductor that is rated for the peak
current anticipated.

1-

VTH "" VZl

+V'N

....;;.;........-

11

.......-

+ 2VBE (01)

....~ LM2576 -XX
+

68p.H

.,

1N5822

CoUT
2200p.F

ZI

-12V@O.7A
REGULATED
OUTPUT

TLlH/11476-14

FIGURE 10. Inverting Buck-Boost Develops -12V
Also, the maximum voltage appearing across the regulator
is the absolute sum of the input and output voltage. For a
-12V output, the maximum input voltage for the LM2576 is
+ 28V, or + 48V for the LM2576HV.
The Switchers Made Simple (version 3.0) design software
can be used to determine the feasibility of regulator designs
using different topologies, different input-output parameters,
different components, etc.

TLlH/11476-16

Note: Complete circuit not shown.

FIGURE 12. Undervoltage Lockout for Buck Circuit

3-83

> ,----------------------------------------------------------------------,
%

Ie
~

::E

.....

~
.....
::E

Additional Applications (Continued)
+VIN

...;;;......Rl

20k

+VIN
....--~,~

+

LM2576-XX

!C.

20k

ADJUSTABLE OUTPUT, LOW-RIPPLE
POWER SUPPLY
A 3A power supply that features an adjustable output voltage is shown in Figure 15. An additional L-C filter that reduces the output ripple by a factor of 10 or more is included in
this circuit.

3 GND

~N

ZI
+VIN

+VIN
1

LM2576-XX

0.1 ).IF

-VOUT

SON/OFF

+
TL/H/11476-17

GNIOO).lF

Noto: Complete circuit not shown (see Figure 10).

Ro

47k

FIGURE 13. Undervoltage Lockout
for Buck-Boost Circuit
TLlH/11476-1B

DELAYED STARTUP
The ON/OFF pin can be used to provide a delayed startup
feature as shown in Figure 14. With an input voltage of 20V
and for the part values shown, the circuit provides approximately 10 ms of delay time before the circuit begins switchIng. Increasing the RC time constant can provide longer delay times. But excessively large RC time constants can
cause problems with input voltages that are high in 60 Hz or
120 Hz ripple, by coupling the ripple into the ON/OFF pin.

Noto: Complete circuit not shown.

FIGURE 14. Delayed Startup

FEEDBACK
SSV
UNREGULATED
DC INPUT

+VIN

OUTPUT
+ GN

I'"

-------.

4

LM2576HV-ADJ
3 GND

2
SON/OFF

, VOLTAGE
..........----=''--+-1.2 10 SOV

R2
SDk
01
lNS822

I OUTPUT

L2

L1

r'"

+ Cl

Rl
1.21k

:

@3A

I""!
- ,
------_.

op lonal oulpul ripple filler
TL/H/11476-19

FIGURE 15.1.2V to 55V Adjustable 3A Power Supply with Low Output Ripple

3-84

Definition of Terms
BUCK REGULATOR

EQUIVALENT SERIES INDUCTANCE (ESL)

A switching regulator topology in which a higher voltage is
converted to a lower voltage. Also known as a step-down
switching regulator.

The pure inductance component of a capacitor (see Figure
16). The amount of inductance is determined to a large
extent on the capaCitor's construction. In a buck regulator,
this unwanted inductance causes voltage spikes to appear
on the output.

BUCK-BOOST REGULATOR
A switching regulator topology in which a positive voltage is
converted to a negative voltage without a transformer.

OUTPUT RIPPLE VOLTAGE
The AC component of the switching regulator's output voltage. It is usually dominated by the output capaCitor's ESR
multiplied by the inductor's ripple current (aIINO)' The peakto-peak value of this sawtooth ripple current can be determined by reading the Inductor Ripple Current section of the
Application hints.

DUTY CYCLE (D)
Ratio of the output switch's on-time to the oscillator period.

for buck regulator

for buck-boost regulator

D = toN = VOUT

T

D = tON =
T

VIN

CAPACITOR RIPPLE CURRENT

Ivol
Ivol + VIN

RMS value of the maximum allowable alternating current at
which a capaCitor can be operated continuously at a specified temperature.

CATCH DIODE OR CURRENT STEERING DIODE
The diode which provides a return path for the load current
when the LM2576 switch is OFF.

STANDBY QUIESCENT CURRENT (ISTBY)
Supply current required by the LM2576 when in the standby
mode (ON/OFF pin is driven to TTL-high voltage, thus turning the output switch OFF).

EFFICIENCY ("I)
The proportion of input power actually delivered to the load.
POUT

"I

POUT

INDUCTOR RIPPLE CURRENT (aIINO)
The peak-to-peak value of the inductor current waveform,
typically a sawtooth waveform when the regulator is operating in the continuous mode (vs. discontinuous mode).

= ~ = POUT + PLOSS

CAPACITOR EQUIVALENT SERIES RESISTANCE (ESR)
The purely resistive component of a real capacitor's impedance (see Figure 16). It causes power loss resulting in capaCitor heating, which directly affects the capacitor's operating lifetime. When used as a switching regulator output
filter, higher ESR values result in higher output ripple voltages.

CONTINUOUS/DiSCONTINUOUS MODE OPERATION
Relates to the inductor current. In the continuous mode, the
inductor current is always flowing and never drops to zero,
vs. the discontinuous mode, where the inductor current
drops to zero for a period of time in the normal switching
cycle.
INDUCTOR SATURATION

TL/H/11476-20

FIGURE 16_ Simple Model of a Real CapaCitor

The condition which exists when an inductor cannot hold
any more magnetiC flux. When an inductor saturates, the
inductor appears less inductive and the resistive component
dominates. Inductor current is then limited only by the DC
resistance of the wire and the available source current.

Most standard aluminum electrolytic capaCitors in the
100 jJoF-1000 jJoF range have 0.50 to 0.10 ESR. Highergrade capacitors ("Iow-ESR", "high-frequency", or "low-inductance"') in the 100 jJoF-1000 jJoF range generally have
ESR of less than 0.150.

OPERATING VOLT MICROSECOND CONSTANT (EoTop)
The product (in Volte jJos) of the voltage applied to the inductor and the time the voltage is applied. This EeTop constant
is a measure of the energy handling capability of an inductor
and is dependent upon the type of core, the core area, the
number of turns, and the duty cycle.

3-85

> ,----------------------------------------------------------------------,
Connection Diagrams
~

::c

In
N

(XX indicates output voltage option. See ordering information table for complete part number.)

:::E

Straight Leads
5-Lead TO-220 (T)
Top View

...I

~
In
N

:i

Bent, Staggered Leads
5-Lead TO-220 (T)
Top View

;'H"'''
-""".•

151 .1 ;'-"""
H

......

3- Ground
2- Output
1- VIN

3- Ground
2- Output
1-VIN

TL/11476-22

TL/11476-21

LM2576T-XX or LM2576HVT-XX
NS Package Number T05A

_

Side View

fL.

PINS 1,3,&:5

~PINS2&:4
TU11476-23

LM2576T-XX Flow LB03
or LM2576HVT-XX Flow LB03
NS Package Number T05D

Ordering Information
Package
Type
5-Lead TO-220
Straight Leads

5-Lead TO-220
Bent and
Staggered Leads

NSC
Package
Number
T05A

T05D

Standard
Voltage Rating
(40y)

High
Voltage Rating
(60y)

LM2576T-3.3
LM2576T-5.0
LM2576T-12
LM2576T-15
LM2576T-ADJ

LM2576HVT-3.3
LM2576HVT-5.0
LM2576HVT-12
LM2576HVT-15
LM2576HVT-ADJ

LM2576T-3.3 Flow LB03
LM2576T-5.0 Flow LB03
LM2576T-12 Flow LB03
LM2576T-15 Flow LB03
LM2576T-ADJ Flow LB03

LM2576HVT-3.3 Flow LB03
LM2576HVT-5.0 Flow LB03
LM2576HVT-12 Flow LB03
LM2576HVT-15 Flow LB03
LM2576HVT-ADJ Flow LB03

3-86

Temperature
Range

-40'C
:S: TJ:S:
+ 125'C

~National

Semiconductor

LM 1577/lM2577 Series
SIMPLE SWITCHER™ Step-Up Voltage Regulator
General Description

Features

The LM1577/LM2577 are monolithic integrated circuits that
provide all of the power and control functions for step-up
(boost), flyback, and forward converter switching regulators.
The device is available in three different output voltage versions: 12V, 15V, and adjustable.

•
•
•
•

Requires few external components
NPN output switches 3.0A, can stand off 65V
Wide input voltage range: 3.5V to 40V
Current-mode operation for improved transient
response, line regulation, and current limit
• 52 kHz internal oscillator
• Soft-start function reduces in-rush current during
start-up
• Output switch protected by current limit, under-voltage
lockout, and thermal shutdown

Requiring a minimum number of external components,
these regulators are cost effective, and simple to use. Listed
in this data sheet are a family of standard inductors and
flyback transformers designed to work with these switching
regulators.
Included on the chip is a 3.0A NPN switch and its associated protection circuitry, consisting of current and thermal limiting, and undervoltage lockout. Other features include a 52
kHz fixed-frequency oscillator that requires no external components, a soft start mode to reduce in-rush current during
start-up, and current mode control for improved rejection of
input voltage and output load transients.

Typical Applications
• Simple boost regulator
• Flyback and forward regulators
• Multiple-output regulator

Typical Application
lN5821

lOOI'H
+5Y
INPUT

51 YIN

O.lI'FI

--

4

2.2k

t-

--

.

2

~ LM2577-ADJ

i

~~

SWITCH

COMP

0.331' F

.....r

I

FEEOBACK

NO

Rl
17.4k

R2
2k

-=--

1
.1.

12Y@$800rnA
REGULATED OUTPUT
Your = 1.23Y (1 + R1/R2)

680I'F

Note: Pin numbers shown
are for TO-220 (T) package.

TL1H/1146B-1

Ordering Information
Package Type

NSCPackage
Drawing

5-Lead TO-220, Straight Leads

T05A

LM2577T-12, LM2577T-15, or
LM2577T-ADJ

5-Lead TO-220
Bent, Staggered Leads

T05D

LM2577T-12 Flow LB03, LM2577T-15 Flow LB03,
or LM2577T-ADJ Flow LB03

16-Pin Molded DIP

N16A

LM2577N-12, LM2577N-15, or
LM2577N-ADJ

24-Pin Surface Mount

M24B

LM2577M-12, LM2577M-15, or
LM2577M-ADJ

4-PinTO-3

K04A

LM1577K-12/883, LM1577K-15/883, or
LM1577K-ADJ/883

Order Number

3-87

Temperature
Range

-40'C

s: TJ s:

+125'C

-55'C

s: TJ s:

+150'C

Absolute Maximum Ratings

Operating Ratings

(Note 1)

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage

Supply Voltage

Output Switch Voltage

65V
6.0A

Power Dissipation

OV

S;

VIN

S;

40V

VSWITCH

S;

60V

Output Switch Current

45V

Output Switch Current (Note 2)

3.5V

Output Switch Voltage
Junction Temperature Range
LM1577
LM2577

S;

ISWITCH
-55'C
-40'C

S;
S;

TJ
TJ

S;
S;

S;

3.0A

+ 150'C
+125'C

Internally Limited

Storage Temperature Range

-65'C to + 150'C

Lead Temperature (Soldering, 10 sec.)

260'C

Maximum Junction Temperature

150'C

Minimum ESD Rating
(C = 100 pF, R = 1.5 kO)

2kV

Electrical Characteristics-LM 1577-12, LM2577-12
Specifications with standard type face are for T J = 25'C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V, and ISWITCH = O.

Symbol

Parameter

Conditions

Typical

LM1577-12
Limit
(Notes 3,4)

LM2577-12
Limit
(Note 5)

11.60/11.40
12.40/12.60

11.60/11.40
12.40112.60

V
V(min)
V(max)

50/100

50/100

mV
mV(max)

50/100

50/100

mV
mV(max)

Units
(Limits)

SYSTEM PARAMETERS Circuit of Figure 1 (Note 6)
VOUT

AVOUT

Output Voltage

Line Regulation

AVIN
AVOUT

Load Regulation

ALOAD
'Ij

Efficiency

VIN = 5V to 10V
ILOAD = 100 mA to 800 mA
(Note 3)

12.0

VIN = 3.5Vto 10V
ILOAD = 300 mA

20

VIN = 5V
ILOAD = 100 mA to 800 mA

20

VIN = 5V, ILOAD = 800 mA

80

VFEEDBACK = 14V (Switch Off)

7.5

%

DEVICE PARAMETERS
Is

Input Supply Current

ISWITCH = 2.0A
VCOMP = 2.0V (Max Duty Cycle)
Vuv

fo

VREF

AVREF
AVIN

Input Supply
Undervoltage Lockout

ISWITCH = 100 mA

Oscillator Frequency

Measured at Switch Pin
ISWITCH = 100 mA

10.0/14.0

mA
mA(max)

50/85

50/85

mA
mA(max)

2.70/2.65
3.10/3.15

2.7012.65
3.10/3.15

V
V(min)
V(max)

48/42
56/62

48/42
56/62

kHz
kHz(min)
kHz(max)

11.76/11.64
12.24/12.36

11.76/11.64
12.24/12.36

V
V(min)
V(max)

25
2.90

52

Output Reference
Voltage

Measured at Feedback Pin
VIN = 3.5V to 40V
VCOMP = 1.0V

Output Reference
Voltage Line Regulator

VIN = 3.5V to 40V

12

7

mV

9.7

k!1

RFB

Feedback Pin Input
Resistance

GM

Error Amp
Transconductance

ICOMP = -30 fLA to +30 fLA
VCOMP = 1.0V

370

Error Amp
Voltage Gain

VCOMP = 1.1Vt01.9V
RCOMP = 1.0 M!1
(Note 7)

80

AVOL

10.0/14.0

3-88

225/145
515/615

225/145
515/615

fL mho
fLmho(min)
fLmho(max)

50/25

50/25

VIV
VIV(min)

Electrical Characteristics-LM 1577-12, LM2577 -12 (Continued)
Specifications with standard type face are for TJ = 25'C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V, and ISWITCH = O.
Symbol

Parameter

Conditions

Typical

LM1577·12
Limit
(Notes 3, 4)

LM2577·12
Limit
(Note5)

2.2/2.0

2.2/2.0

V
V(min)

0.40/0.55

0.40/0.55

V
V(max)

±130/±90
±300/±400

±130/±90
±300/±400

IJ-A
IJ-A(min)
IJ-A(max)

2.5/1.5
7.5/9.5

2.5/1.5
7.5/9.5

IJ-A
IJ-A(min)
IJ-A(max)

93/90

93/90

%
%(min)

Units
(Limits)

DEVICE PARAMETERS (Continued)
Error Amplifier
Output Swing

Upper Limit
VFEEDBACK

2.4

= 10.0V

Lower Limit
VFEEDBACK
Error Amplifier
Output Current
Iss

D

Soft Start Current

Maximum Duty Cycle

0.3

= 15.0V
VFEEDBACK = 1O.OV to 15.0V
VCOMP = 1.0V

±200

VFEEDBACK = 10.0V
VCOMP = OV

5.0

VCOMP = 1.5V
ISWITCH = 100 mA

95

.6. ISWITCH
.6.VCOMP

Switch
Transconductance

IL

Switch Leakage
Current

VSWITCH = 65V
VFEEDBACK = 15V (Switch Off)

10

Switch Saturation
Voltage

ISWITCH = 2.0A
VCOMP = 2.0V (Max Duty Cycle)

0.5

VSAT

12.5

NPN Switch
Current Limit

AN

300/600

300/600

IJ-A
IJ-A(max)

0.7/0.9

0.7/0.9

V
V(max)

3.7/3.0
5.3/6.0

3.7/3.0
5.3/6.0

A
A(min)
A(max)

4.5

3·69

Electrical Characteristics-LM1577-15, LM2577-15
Specifications with standard type face are for TJ = 25°C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V, and ISWITCH = O.

Symbol

Parameter

Typical

Conditions

LM1577-15
Limit
(Notes 3, 4)

LM2577-15
Limit
(Note 5)

14.50/14.25
15.50/15.75

14.50/14.25
15.50/15.75

V
V(min)
V(max)

50/100

50/100

mV
mV(max)

50/100

50/100

mV
mV(max)

Units
(Limits)

SYSTEM PARAMETERS Circuit of Figure 2 (Note 6)
VOUT

aVOUT

Output Voltage

Line Regulation

VIN
aVOUT

Load Regulation

alLOAD

"7/

Efficiency

VIN = 5Vto 12V
ILOAD = 100 mA to 600 mA
(Note 3)

15.0

VIN = 3.5V to 12V
ILOAD = 300 mA

20

VIN = 5V
ILOAD = 100 mA to 600 mA

20

VIN

=

5V, ILOAD

=

600 mA

%

80

DEVICE PARAMETERS
Is

Input Supply Current

VFEEDBACK
(Switch Off)

=

7.5

1B.OV

10.0/14.0

ISWITCH = 2.0A
VCOMP = 2.0V
(Max Duty Cycle)
VUY

fo

Input Supply
Undervoltage
Lockout
Oscillator Frequency

ISWITCH

aVREF
aVIN

25

=

Output Reference
Voltage

Measured at Feedback Pin
VIN = 3.5V to 40V
VCOMP = 1.0V

Output Reference
Voltage Line Regulation

VIN

=

3.5V to 40V

RFB

Feedback Pin Input
Voltage Line Regulator

GM

Error Amp
Transconductance

ICOMP = -30 ",A to +30 ",A
VCOMP = 1.0V

Error Amp
Voltage Gain

VCOMP = 1.1Vto1.9V
RCOMP = 1.0 MO
(Note 7)

AYOL

50/85

50/85

mA(max)

2.70/2.65
3.10/3.15

2.70/2.65
3.10/3.15

V
V(min)
V(max)

4B/42
56/62

48/42
56/62

kHz
kHz(min)
kHz(max)

14.70/14.55
15.30/15.45

14.70/14.55
15.30/15.45

V
V(min)
V(max)

52

100 mA

15

10

mV

12.2

kO

300

170/110
420/500

1701110
420/500

",mho
",mho(min)
",mho(max)

40/20

40/20

VIV
VIV(min)

65

3-90

mA
mA(max)
mA

2.90

100 mA

Measured at Switch Pin
ISWITCH

VREF

=

10.0/14.0

Electrical Characteristics-LM1577-15, LM2577.. 15 (Continued)
Specifications with standard type face are for TJ = 25·C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V, and ISWITCH = O.
Symbol

Parameter

Conditions

Typical

LM1577-15
Limit
(Notes 3, 4)

LM2577-15
Limit
(Note 5)

2.2/2.0

2.2/2.0

V
Vlmin)

0.4/0.55

0.40/0.55

V
V(max)

±130/±90
±300/±400

±130/±90
±300/±400

p.A
p.A(min)
p.A(max)

2.5/1.5
7.5/9.5

2.5/1.5
7.5/9.5

p.A
p.A(min)
p.A(max)

93/90

93/90

%
%(min)

Units
(Limits)

DEVICE PARAMETERS (Continued)
Error Amplifier
Output Swing

Upper Limit
VFEEDBACK

2.4

= 12.0V

Lower Limit
VFEEDBACK
Error Amp
Output Current
IsS

D
~lsWITCH
~VCOMP

IL

VSAT

Soft Start Current

Maximum Duty
Cycle

0.3

= 18.0V
VFEEDBACK = 12.0V to 18.0V
VCOMP = 1.0V

±200

VFEEDBACK = 12.0V
VCOMP = OV

5.0

VCOMP = 1.5V
ISWITCH = 100 mA

95

Switch
Transconductance

12.5

Switch Leakage
Current

VSWITCH = 65V
VFEEDBACK = 18.0V
(Switch Off)

10

Switch Saturation
Voltage

ISWITCH = 2.0A
VCOMP = 2.0V
(Max Duty Cycle)

0.5

NPNSwitch
Current Limit

VCOMP

= 2.0V

AN
p.A
300/600

300/600

p.A(max)

0.710.9

0.7/0.9

V(max)

3.7/3.0
5.3/6.0

3.713.0
5.3/6.0

A
A(min)
A(max)

V

4.3

3-91

Electrical Characteristics-LM 1577-ADJ, LM2577-ADJ
Specifications with standard type face are for TJ = 25'C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, Y,N = 5V, VFEEDBACK = VREF, and ISWITCH = O.
Symbol

Parameter

Conditions

Typical

LM1577·ADJ
Limit
(Notes 3, 4)

LM2577·ADJ
Limit
(Note 5)

11.60/11.40

12.40/12.60

11.60/11.40
12.40/12.60

V
V(min)
V(max)

50/100

50/100

mV
mV(max)

50/100

50/100

mV
mV(max)

Units
(Limits)

SYSTEM PARAMETERS Circuit of Figure 3 (Note 6)
VOUT

I:.vOUTI

Output Voltage

Line Regulation

~V'N

1::"vOUT/

Load Regulation

~ILOAD

'11

Efficiency

Y,N = 5Vto 10V
ILOAD = 100 mA to 800 mA
(NoteS)

12.0

Y,N = S.5V to 10V
ILOAD = SOO mA

20

Y,N = 5V
ILOAD = 100 mA to 800 mA

20

= 5V, ILOAD = 800 mA

80

Y,N

%

DEVICE PARAMETERS
IS

Input Supply Current

VFEEDBACK

= 1.5V (Switch Off)

ISWITCH = 2.0A
VCOMP = 2.0V (Max Duty Cycle)
Vuv

fo

VREF

~VREF/

~V'N

IB
GM

AVOL

= 100 mA

Input Supply
Undervoltage Lockout

ISWITCH

Oscillator Frequency

Measured at Switch Pin
ISWITCH = 100 mA

7.5
10.0/14.0

10.0/14.0

mA
mA(max)

50/85

50/85

mA
mA(max)

2.70/2.65
3.10/3.15

2.70/2.65
3.10/3.15

V
V(mln)
V(max)

48/42
56/62

48/42
56/62

kHz
kHz(mln)
kHz(max)

1.214/1.206
1.246/1.254

1.214/1.206
1.246/1.254

V
V(min)
V(max)

25
2.90

52

Reference
Voltage

Measured at Feedback Pin
Y,N = 3.5Vto 40V
VCOMP = 1.0V

Reference Voltage
Line Regulation

Y,N

Error Amp
Input Bias Current

VCOMP

Error Amp
Transconductance

ICOMP = -30 ""A to +30 ""A
VCOMP = 1.0V

Error Amp
Voltage Gain

VCOMP
RCOMP

Error Amplifier
Output Swing

Upper Limit
VFEEDBACK

= 1.0V

Lower Limit
VFEEDBACK

= 1.5V

= 3.5V to 40V

1.230

0.5

= 1.0V

mV

100

= 1.lVto 1.9V
= 1.0 MO (Note 7)

300/800

300/800

nA
nA(max)

2400/1600
4800/5800

2400/1600
4800/5800

""mho
""mho(min)
""mho(max)

500/250

500/250

V/V
V/V(min)

2.2/2.0

2.2/2.0

V
V(mln)

0.40/0.55

0.40/0.55

V
V(max)

3700

800
2.4
0.3

3·92

r-

Electrical Characteristics-LM1S77-ADJ, LM2S77-ADJ

....s::U1

(Continued)

Specifications with standard type face are for TJ = 25"C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V, VFEEDBACK = VREF, and ISWITCH = O.
Symbol

Parameter

Conditions

Typical

LM1577-ADJ
Limit
(Notes 3, 4)

LM2577-ADJ
Limit
(Note 5)

Units
(Limits)

Iss

D

VFEEDBACK = 1.0V to 1.5V
VCOMP = 1.0V

Soft Start Current

VFEEDBACK = 1.0V
VCOMP = OV

5.0

VCOMP = 1.5V
ISWITCH = 100 mA

95

Maximum Duty Cycle

±200

~ISWITCH/
~VCOMP

Switch
Transconductance

IL

Switch Leakage
Current

VSWITCH = 65V
VFEEDBACK = 1.5V (SWitch Off)

10

Switch Saturation
Voltage

ISWITCH = 2.0A
VCOMP = 2.0V (Max Duty Cycle)

0.5

NPNSwitch
Current Limit

VCOMP = 2.0V

4.3

VSAT

±130/±90
±300/±400

±130/±90
±300/±400

".A
".A(min)
".A(max)

2.5/1.5
7.5/9.5

2.5/1.5
7.5/9.5

".A
".A(min)
".A(max)

93/90

93/90

%
%(min)

AN

12.5

300/600

300/600

".A
".A(max)

0.7/0.9

0.7/0.9

V
V(max)

3.7/3.0
5.3/6.0

3.7/3.0
5.3/6.0

A
A(min)
A(max)

THERMAL PARAMETERS (All Versions)
K Package, Junction to Ambient
K Package, Junction to Case

35
1.5

IIJA
IIJC

T Package, Junction to Ambient
T Package, Junction to Case

65
2

IIJA

N Package, Junction to
Ambient (Note 8)

85

IIJA

M Package, Junction
to Ambient (Note 8)

100

IIJA
IIJC

Thermal Resistance

"C/W

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating ratings indicate conditions the device is intended to
be functional, but device parameter specifications may not be guaranteed under these conditions. For guaranteed specifications and test conditions, see the
Electrical Characteristics.
Note 2: Due to timing considerations of the LM1577/LM2577 current limit circuit, output current cannot be internally limited when the LM1577/LM2577 is used as a
step·up regulator. To prevent damage to the switch, its current must be externally limited to 6.0A. However, output current is internally limited when the

LMI577/LM2577 is used as a flyback or forward converter regulator in accordance to the Application Hints.
Nole 3: All limits guaranteed at room temperature (standard type face) and at temperature extremes (boldface Iype). All limits are used to calculate Outgoing
Quality Level, and are 100% production tested.
Nole 4: A military RETS electrical lesl specificalion is available on request. AI Ihe time of printing, the lMI577K-12/883, lMI577K·15/883, and
LMI577K·ADJ/883 RETS specifications complied fully with the boldface limits in these columns. The lMI577K·12/883, lMI577K·15/883, and LMI577K·ADJI
883 may also be procured to Standard Military Drawing specifications.
Note 5: All limits guaranteed at room temperature (standard type face) and at temperature extremes (boldface type). All room temperature limits are 100%

production tested. All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods.
Note 6: External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the LM1577/LM2577 is
used as shown in the Test CirCUit, system performance will be as specified by the system parameters.
Note 7: A 1.0 Mn resistor is connected to the compensation pin (which is the error amplifier'S output) to ensure accuracy in measuring AVOL. In actual applications,
this pin's load resistance should be 2' 10 MO, resulting in AVOL that is typically twice the guaranteed minimum limit.
Note 8: JUnction to ambient thermal resistance with approximately 1 square inch of pc board copper surrounding the leads. Additional copper area will lower
thermal resistance further. See thermal model in "Switchers Made Simple" software.

3-93

r-

s::

N
U1

.......

.......

en
CD

DEVICE PARAMETERS (Continued)
Error Amp
Output Current

.......

.......
......

....
~l

o

CU

";:

~

r---------------------------------------------------------------------------------,
Typical Performance Characteristics

r-.
r-.

Reference Voltage
vs Temperature

II)

C'I

1.240

...I

1.238

:E

t::
r-.

~

1.236

~g

1.232

....

w

...I

w

II)

:E

u

~

12.10

AOJ VERSIONS

1.230
1.228
1.226
1.224

~

I---'

g

/'

w

a
~

1.222

-50 -25 0

25

50

12.04
12.00

14.92
14.90

0

1/ ......

lj

o. 1

~

-0. 1

./

~
~

/

I

1

o

W

g

~

25

~

~

4.0

~
~
~

"

3500
3000

2500
-50 -25 0

g
tl
is

./

1.0

/

;.
W

~ 1200

w

~g

~

~

~
~

I'. .......
I-

g

"

400
350

......

1000

0.0

I

-1.0

o

"

~

r-...

5

W

300
275

r-....

r-....

. . . 1'--

25 50 75 100 125 150

TEMPERATURE (oc)

~

120

~

100

"

r-....
25 50

80
60
-50 -25 0

25 50

75 100 125 150

TEMPERATURE (oc)

75 100 125 150

TEMPERATURE (oC)

Error Amp Voltage
Gain vs Temperature
I

">

~

120

~

100

~
g

80

z

I'. ......

~

r-....

140

I'--

~

225
200
-50 -25 0

75 100 125 150

"cOMP;o 10MIl

~

"- I......

160

"

25

15V VERSIONS

325

Error Amp Voltage
Gain vs Temperature

140

~

Error Amp Transconductance
vs Temperature

TEMPERATURE (Oc)

~z

g

m250

~
25 50

V

12V VERSIONS

800
600
-50 -25 0

,/

1.0

375

w
z

250

160
"cOMP;o 10MI!

.........

/'

2.0

S 350 "-

,

300

200
-50 -25 0

25 50 75 100 125 150

"r-.....

3.0

400

lBO

[\,

:.---

SUPPLY VOLTAGE (V)

Error Amp Transconductance
vs Temperature

AOJ VERSIONS

1400

~

450

Error Amp Voltage
Gain vs Temperature

z

25

12V VERSIONS

">

1800

~

~

g

/'

4.0

-2.0
5

TEMPERATURE (Oc)

.::.

~

....... i""
2.0

500

3
~

1"'\

4000

1600

w

5.0

SUPPLY VOLTAGE (V)

A~J v~RSI6NS
w
u
z

15V VERSIONS

">
.5-

/ ' I-'

3.0

o

Error Amp Transconductance
vs Temperature

75 100 125 150

vs Supply Voltage

12V VERSIONS

~

50

t. Reference Voltage

-2.0
5

25

6.0

SUPPLY VOLTAGE (V)

:3

-50 -25 0

TEMPERATURE (Oc)

m
I
.. -1.0

-0.2

4500

50 75 100 125 150

t. Reference Voltage
vs Supply Voltage

. / V-

0.2

5000

25

TEMPERATURE (oc)

ADJ VERSIONS

0.3

-

V

~ 14.9"

5.0

g

~

~ 14.9 8
14.96

f5

11.94

t. Reference Voltage
vs Supply Voltage

-

./

./

~ 15.00

11.96

0.5
0.4

1.5.04

~ 15.02

./

1..--"-

11.98

TEMPERATURE (oc)

~

~

~

12.02

11.90
-50 -25

75 100 125 150

15V VERSIONS

15.08

:E 15.06

12.06

11.92

1.220

1

Reference Voltage
Temperature

15.10 vs

12V VERSIONS

12.08

~

-

1.234

Reference Voltage
vs Temperature

5~ VE~SIO~S

"coMP" 10 Mil

~

"

.......

60
40
-50 -25 0

r-....

r-... I-

25 50 75 100 125 150

TEMPERATURE (oc)
TL/HI1146B-2

3·94

.Typical Performance Characteristics

....

==
en

(Continued)

.......

50

Supply Current
vs Temperature

';(

40

~
i3

30

.s
~

~

20
15

.....

I'.

r--.

'SWITCH

= 3A

1

45

'S"~H ,! 2A I-

~

i3

'SWITCH = IA

~

25

~

= 100 mA

-50 -25 0

25 50

/

o

0.5

1.6

1.0

1 1
1
,,\ 1/ 125

~

1."

~

i

0.7

1.2 ' { \ .

1.

z

0.6
0.5

~

0.4

2
~

O~ :"'== .....

~
0.6 -55
0.8

0.4

O.2

o

~

1
1

1
2.5

,.v
"- ,........-~
-5S C

~

12

~

i

1.0

1.5

2.0

2.5

5.

20 0

53

\

"N

!

I'\,

S

'\,

~_

[\..

100

'"

BO
60
-50 -25 0

25

r......

52

I"' r-....

1
10

8
-50 -25 0

3.0

25 50

"-

r\

75 100 125 150

Feedback Pin Bias
Current vs Temperature

11

r r\

ADJ VERSIONS

\
1\

50

j

49

"r-47
-50 -25 0

TEMPERATURE (ac)

"

TEMPERATURE (ac)

V

50 75 100 125 150

50 75 100 125 150

r-.. .......

SWITCH CURRENT (A)

22 0

120

t!

%'

Oscillator Frequency
vs Temperature

~ 140

13

~
0.5

25

Switch Transconductance
vs Temperature

$

~,

CURRENT LIMIT OVERDRIVE (mA)

~ 160

25°C
-40°C

>"
....

a

.4fIP /.

100 200 300 400 500 600 700 800

18 o

1.

12soe

.AP'

0.2

m

.......

3.5

1

0.3

iii"

........

TEMPERATURE (ac)

ISOOC

~

....~

I'-..

4.0

3.0
-50 -25 0

3.0 (A)

Switch Saturation Voltage
vs Switch Current

O. 1

:!

4.5

D = 0.2

2.0

0.8

~

:;:

1.5

I

L.

.......

0.9

,\ 150

j
;:

1.0

.......

SWITCH CURRENT (A)

Current Limit Response
Time vs Overdrive
1.B

.....

V

...-: ........
10

TEMPERATURE (ac)

2.0

==
en

N

.......

:i
::;

D=~

,/

15

75 100 125 150

.-

~

0=0.9

20

5

3:

./

30

1 1 1

o

.......
.......

Current Limit
vs Temperature

I\.

40
35

'SWITCH

10

5.0

50

50" OUTY CYCL~

35
25

55

1 1 1

45

Supply Current
vs Switch Current

25 50 75 100 125 150

TEMPERATURE (ac)
TL/H/11468-3

3-95

•

Connection Diagrams
Straight Leads
5-Lead TO-220 Ie: Pin numbers shown
are for T0-220 (T) package
'Reslstors are Internal
Ie LM1577/LM2577 for
12V and 15V versions.

Rl'

R2'

TL/H/TT468-TO

FIGURE 4. LM1577/LM2577 Block Diagram and Boost Regulator Application
STEP-UP (BOOST) REGULATOR
Figure 4 shows the LM1577-AOJ/LM2577-AOJ used as a
Step-Up Regulator. This is a switching regulator used for
producing an output voltage greater than the input supply
voltage. The LM1577.12/LM2577-12 and LM1577-151
LM2577-15 can also be used for step-up regulators with
12V or 15V outputs (respectively), by tying the feedback pin
directly to the regulator output.
A basic explanation of how it works is as follows. The
LM1577/LM2577 turns its output switch on and off at a frequency of 52 kHz, and this creates energy in the inductor
(L). When the NPN switch turns on, the inductor current
charges up at a rate of VIN/L, storing current in the inductor.

When the switch turns off, the lower end of the inductor flies
above VIN, discharging its current through diode (0) into the
output capacitor (COUT) at a rate of (VOUT - VIN)/L. Thus,
energy stored in the inductor during the switch on time is
transferred to the output during the switch off time. The out·
put voltage is controlled by the amount of energy transferred which, in turn, is controlled by modulating the peak
inductor current. This is done by feeding back a portion of
the output voltage to the error amp, which amplifies the difference between the feedback voltage and a 1.230V reference. The error amp output voltage is compared to a voltage proportional to the switch current (i.e., inductor current
during the switch on time).

3-98

r3:
......

Application Hints (Continued)
The comparator terminates the switch on time when the two
voltages are equal, thereby controlling the peak switch current to maintain a constant output voltage.
Voltage and current waveforms for this circuit are shown in
Figure 5, and formulas for calculating them are given in Figure6.

Before proceeding any further, determine if the LM15771
LM2577 can provide these values of Your and ILOAD(max)
when operating with the minimum value of VIN. The upper
limits for Your and ILOAD(max) are given by the following
equations.
and

SWITCH
VOLTAGE
DIODE
VOLTAGE
INDUCTOR
CURRENT

VSW~rr) - r-,SAT

- -r-T - - _L_l.-J __ L-

OV - - - - - - - - - - - - -

:~ :O::j--t:::
VR -

-

--

1. For 12V or 15V output
From Figure 7a (for 12V output) or Figure 7b (for 15V
output), identify Inductor code for region indicated by
VIN (min) and ILOAD (max). The shaded region indicates
conditions for which the LM1577/LM2577 output switch
would be operating beyond its switch current rating. The
minimum operating voltage for the LM1577/LM2577 is
3.5V.
From here, proceed to step C.

0-------------..=--1- - r-=-T - -

ISW(PK) - - -

DIODE
CURRENT

Io~~-

o _....J __ Ll __ L_

Io(PK)

-t:E.F:E---------- -- -----

0-

-

--

-TL/H/1146B-ll

FIGURE 5. Step-Up Regulator Waveforms
Duty Cycle

o

Average Inductor
Current

IIND(AVE)

Inductor CUrrent
Ripple

IloIIND

Peak Inductor
CUrrent

IIND(PK)

Peak Switch
Current

ISW(PK)

Switch Voltage
WhenOlf

ILOAD

1-0

D(max), the maximum switch duty cycle (0

VIN - VSAT _0_

L
ILOAD

+ IloIIND

1-0

ID(AVE)

Peak Diode
CUrrent

ID(PK)
Po

D

S;

0.9):

2
IloIIND
2

where VF = 0.5V for Schottky diodes and 0.8V for fast
recovery diodes (typically);
E- T, the product of volts x time that charges the inductor:

VOUT - VSAT

E-T = D(max) (VIN(min) - 0.6V)106
(V-,..s)
52,000 Hz
I,ND,DC, the average inductor current under full load;

ILOAD

+

1-0

I

Average Diode
Current

S;

D
- Your + VF - VIN(min)
(max) Your + VF - O.SV

52,000

VSW(OFF)

Diode Reverse
Voltage

Power Dissipation
of lM1577/2577

2. For Adjustable version
Preliminary calculations:
The inductor selection is based on the calculation of the
following three parameters:

VOUT + VF - VIN _ VOUT - VIN
VOUT + VF VSAT - ~

ILOAD

+ IloIIND

1-0
0.2511 (ILOAD) 2 0
1-0

+

_ 1.05 X ILOAD(max)
IND,DC 1 - D(max)

B. Identify Inductor Value:

2

1. From Figure 7c, identify the inductor code for the region
indicated by the intersection of E-T and IIND,DC' This code
gives the inductor value in microhenries. The L or H prefix
signifies whether the inductor is rated for a maximum E-T of
90 V-,..s (L) or 250 V-,..s (H).

ILOAD 0 VIN
50(1-0)

VF = Forward Biased Diode Voltage
ILOAD = Output load Current

2. If D < 0.85, go on to step C. If D "' 0.85, then calculate
the minimum inductance needed to ensure the switching
regulator's stability:

FIGURE 6. Step-Up Regulator Formulas
STEP-UP REGULATOR DESIGN PROCEDURE
The following design procedure can be used to select the
appropriate external components for the circuit in Figure 4,
based on these system requirements.

LMIN = 6.4 (VIN(min) - O.SV) (2D(max) - 1)
(,..H)
1 - D(max)
If LMIN is smaller than the inductor value found in step B1,
go on to step C. Otherwise, the inductor value found in step
B1 is too low; an appropriate inductor code should be obtained from the graph as follows:
1. Find the lowest value inductor that is greater than LMIN.
2. Find where E-T intersects this inductor value to determine if it has an L or H prefix. If E-T intersects both the
Land H regions, select the inductor with an H prefix,

Given:
VIN (min) = Minimum input supply voltage
Your = Regulated output voltage
ILOAO(max) = Maximum output load current

3-99

.....
.....

...
i'

A. Voltage Options:

- -- -l-,\I'No

...,3:

en

en
CD

These limits must be greater than or equal to the values
specified in this application.
1. Inductor Selection (L)

___ J_
~
INO(AVE) - -

SWITCH
CURRENT

Vour';; SOV
Vour';; 10 X VIN(min)
2.1 A x VIN(min)
I
LOAD(max) ,;;
V
our

en
.....
.....
.....
r-

o

.l!
~

r---------------------------------------------------------------------------------,
Application Hints (Continued)

I::

10

~

:i

12

~

~

'"'"~
g

'"'"~

...

...

~
an

....

0

>
0=>
0..
15

0-

:i

=>
0..
15

'"=>
'"

Z
:i

4
3
0.1

IHl'on

I •• '

I."

L3l

J

II

J

~
I~

IJ

~

IJ /

I
V V/

~/

5

"L L

4

ISlll

r]!.

10
B

'"=>
'"Z
:i

5

11

It' ~

~
~
~

3
0.2 0.30.4

0.6 O.B 1.0

0.1

1.75

0.2

MAXIMUM LOAD CURRENT (A)

0.30.4

0.6 O.B 1.0

1.7

MAXIMUM LOAD CURRENT (A)
TL/H/11466-27

TL/H/I146B-2B

FIGURE 7a. LM2577·12 Inductor Selection Guide

FIGURE 7b. LM2577·15 Inductor Selection Guide

E'T (Y. )Js)

IL
LL
:~ " L470,l'{ L330 K

/

50

35

"'./

/

1/

K

\,. ~

1'\ /

30/

L220

)~

~

/
L150

A

"-..../

I'

LV

L

./
K

L100

'\.../

/

L6B

"-....V

/1

L~

25r-~~_+_+~_r~--~r-r-~~_+~~~~~~

/~

/

/

20/
0.3 0.350.40.450.5 0.6 0.7 O.S 0.91.0

V VI

1.5

2.0

2.5

3.0

'iND. DC (A)
TL/H/1146B-12

FIGURE 7c. LMI577·ADJ/LM2577-ADJ Inductor Selection Graph
Nole:
These charts assume that the Inductor ripple current Inductor Is approximately 20% to 30% of the average Inductor current (when the regulator Is under full load).
Greater ripple current causes higher peak switch currents and greater output ripple voltage; lower ripple current is achieved with larger·value Inductors. The factor
of 20 to 30% Is chosen as a convenient balance between the two extremes.

3·100

r-

....
==

Application Hints (Continued)
C. Select an inductor from the table of Figure 8 which crossreferences the inductor codes to the part numbers of three
different manufacturers. Complete specifications for these
inductors are available from the respective manufacturers.
The inductors listed in this table have the following characteristics:

Rc :;;;

C
our"

C

Pulse

Renco
RL2442
RL2443
RL2444
RL1954
RL1953
RL 1952
RL1951
RL1950

H150
H220
H330
H470
H6BO
H1000
H1500
H2200

415 - 0936
430 - 0636
430 -0635
430 - 0634
415 - 0935
415 - 0934
415 - 0933
415 - 0945

PE - 53115
PE - 53116
PE - 53117
PE-53118
PE - 53119
PE - 53120
PE - 53121
PE - 53122

RL2445
RL2446
RL2447
RL1961
RL1960
RL1959
RL195B
RL244B

x

Your

" VIN(min)

x

Rc

x (VIN(min) + (3.74
4B7,BOO x Vour3

x

105 XL))

The larger of these two values is the min mum value that
ensures stability.

C. Calculate the minimum value of Co
5.:.:B..:.5=-X-:-V~o~ur!,.-2_X---:C-"o~u'-!.r
Cc::' .:.
Rc2 x VIN(min)
The compensation capacitor is also part of the soft start
circuitry. When power to the regulator is turned on, the
switch duty cycle is allowed to rise at a rate controlled by
this capacitor (with no control on the duty cycle, it would
immediately rise to 90%, drawing huge currents from the
input power supply). In order to operate properly, the soft
start circuit requires Cc ::, 0.22 /-,F.

Manufacturer's Part Number

PE - 53112
PE - 92114
PE - 92108
PE - 53113
PE - 52626
PE- 52627
PE - 53114
PE-52629

VIN(min)

our

Renco: ferrite, bobbin-core inductors; Benefits are low
cost and best ability to withstand E-T and peak current
above rated value. Be aware that these inductors generate more EMI than the other types, and this may interfere
with signals sensitive to noise.

AlE

_0._1_9_X_L_X_R."c,-X_I",LO",A",D:..(m=ax",)

and

Pulse: powdered iron, toroid core inductors; Benefits are
low EMI and ability to withstand E-T and peak current
above rated value better than ferrite cores.

415 - 0932
415 - 0931
415 - 0930
415 - 0953
415 - 0922
415 - 0926
415 - 0927
415-0928

_
75_0_X_I",LO:,!A:",D",(m.!!!ax~)_X_V...!O~U,-,T_2

B. Calculate the minimum value for COUT using the following
two equations.

low electro-magnetic interference (EM!), small physical
size, and very low power dissipation (core loss). Be careful not to operate these inductors too far beyond their
maximum ratings for E-T and peak current, as this will
saturate the core.

L47
L68
L100
L150
L220
L330
L470
L680

.....
......
r-

VIN(min)2
Select a resistor less than or equal to this value, and it
should also be no greater than 3 kn.

AlE" ferrite, pot-core inductors; Benefits of this type are

Inductor
Code

U1
.....

A. First, calculate the maximum value for RO

The value of the output filter capacitor is normally large
enough to require the use of aluminum electrolytic capacitors. Figure 9 lists several different types that are recommended for switching regulators, and the following parameters are used to select the proper capacitor.

Working Voltage (WVDC): Choose a capacitor with a working voltage at least 20% higher than the regulator output
voltage.
Ripple Current: This is the maximum RMS value of current
that charges the capacitor during each switching cycle. For
step-up and flyback regulators, the formula for ripple current
is
I
- ILOAD(max) X D(max)
RIPPLE(RMS) 1 - D(max)
Choose a capacitor that is rated at least 50% higher than
this value at 52 kHz.

AlE Magnetics, dlv. Vernltron Carp., (813) 347-2181
2801 72nd Street North, SI. Petersburg, FL 33710
Pulse Engineering, (619) 268-2400
P.O. Box 12235, San Diego. CA 92112
Renco Electronics Inc., (516) 586-5566
60 Jeffryn Blvd. East, Deer Park, NY 11729

Equivalent Series Resistance (ESR): This is the primary
cause of output ripple voltage, and it also affects the values
of Rc and Cc needed to stabilize the regulator. As a result,
the preceding calculations for Cc and Rc are only valid if
ESR doesn't exceed the maximum value specified by the
following equations.

FIGURE 8_ Table of Standardized Inductors and
Manufacturer's Part Numbers
2. Compensation Network (Re, Cd and Output Capacitor (COUT) Selection

ESR :;;; 0.01 X 15V and :;;; B.7 X (10)- 3 X VIN
IRIPPLE(P-P)

Rc and Cc form a pole-zero compensation network that
stabilizes the regulator. The values of Rc and Cc are mainly
dependant on the regulator voltage gain, ILOAD(max), Land
COUT. The following procedure calculates values for Rc,
Cc, and COUT that ensure regulator stability. Be aware that
this procedure doesn't necessarily result in Rc and Cc that
provide optimum compensation. In order to guarantee optimum compensation, one of the standard procedures for
testing loop stability must be used, such as measuring VOUT
transient response when pulsing ILOAD. (See Figure 13.)

ILOAD(max)

where
I
_ 1.15 X ILOAD(max)
RIPPLE(P-P) 1 - D(max)
Select a capacitor with ESR, at 52 kHz, that is less than or
equal to the lower value calculated. Most electrolytic capacitors specify ESR at 120 Hz which is 15% to 30% higher
than at 52 kHz. Also, be aware that ESR increases by a
factor of 2 when operating at - 20·C.

3-101

==

N
U1

.....
.....
~
....
(D'
o

Application Hints (Continued)
In general, low values of ESR are achieved by using large
value capacitors (C ~ 470 ",F), and capacitors with high
WVDC, or by paralleling smaller-value capacitors.

ground with a good quality, low ESR, 0.1 ",F capacitor
(leads as short as possible) is normally sufficient.
If the LM1577 is located far from the supply source filter
capacitors, an additional large electrolytic capacitor (e.g.
47 ",F) is often required.
5. Diode Selection (D)

3. Output Voltage Selection (R1 and R2)
This section is for applications using the LM1577-ADJ/
LM2577-ADJ. Skip this section if the LM1577-12/LM257712 or LM1577-15/LM2577-15 is being used.
With the LM1577-ADJ/LM2577-ADJ, the output voltage is
given by

The switching diode used in the boost regulator must withstand a reverse voltage equal to the circuit output voltage,
and must conduct the peak output current of the LM2577. A
suitable diode must have a minimum reverse breakdown
voltage greater than the circuit output voltage, and should
be rated for average and peak current greater than
ILOAD(max) and ID(PK). Schottky barrier diodes are often favored for use in switching regulators. Their low forward voltage drop allows higher regulator efficiency than if a (less
expensive) fast recovery diode was used. See Figure 10 for
recommended part numbers and voltage ratings of 1A and
3A diodes.

Your = 1.23V(1 + R1/R2)
Resistors R1 and R2 divide tile output down so it can be
compared with the LM1577-ADJ/LM2577-ADJ internal
1.23V reference. For a given desired output voltage Vour,
select R 1 and R2 so that
R1 = Your _ 1
R2
1.23V
4. Input Capacitor Selection (CIN)
The switching action in the step-up regulator causes a triangular ripple current to be drawn from the supply source. This
in turn causes noise to appear on the supply voltage. For
proper operation of the LM1577, the input voltage should be
decoupled. Bypassing the Input Voltage pin directly to

Your
(max)

Cornell Dublier-Types 239, 250, 251, UFT, 300,
or 350
P.O. Box 128, Pickens, SC 29671
(803) 878-6311
Nichlcon-Types PF, PX, or PZ
927 East Parkway, Schaumburg, IL 60173
(708) 843-7500

Fast Recovery
3A

20V

1N5817
MBR120P

1N5820
MBR320P

30V

1N5818
MBR130P
11D003

1N5821
MBR330P
31D003

40V

1N5819
MBR140P
11D004

1N5822
MBR340P
31 D004

MBR150
11D005

MBR350
31 D005

Sprague-Types 672D, 673D, or 674D
Box 1, Sprague Road, Lansing, NC 28643
(919) 384-2551

50V

United Chemi-Con-Types LX, SXF, or SXJ
9801 West Higgins Road, Rosemont, IL 60018
(708) 696-2000

100V

FIGURE 9. Aluminum Electrolytic Capacitors
Recommended for Switching Regulators

Schottky
1A

1A

1N4933
MUR105
1N4934
HER102
MUR110
10DL1

FIGURE 10. Diode Selection Chart

3-102

3A

MR851
30DL1
MR831
HER302

Application Hints

r3:
.....

(Continued)

U1

cal performance of this regulator is shown in Figures 12 and
13. The switching waveforms observed during the operation
of this circuit are shown in Figure 14.

BOOST REGULATOR CIRCUIT EXAMPLE
By adding a few external components (as shown in Figure
11), the LM2577 can be used to produce a regulated output
voltage that is greater than the applied input voltage. Typi-

......
......

r3:
I\)
U1

......
......
rn
CD
..,.

iii'
III

TL/H/11468-13

Note: Pin numbers shown are for TO·220

m package.

FIGURE 11. Step-up Regulator Delivers 12V from a 5V Input
11.990

Rt.

= 150

11.985

~ 11.980
~

'"~

11.975

0

11.970

~

11.965

0

11.960

...>
'"

r--...

I'- r-...

--i'-..

11.955
11.950
4.0 5.0 6.0 7.0 8.0 9.0 10.0 11.0

INPUT VOLTAGE (V)

TL/H111468-14

FIGURE 12. Line Regulation (Typical) of Step-Up Regulator of Figure 11

A

Ar o:

(0

B[ 2:
soomA

B

[

c[

2:

DC

0

400mA

TL/H111468-16

FIGURE 14. Switching Waveforms of Step-Up
Regulator of Figure 11

TL/H111468-15

FIGURE 13. Load Transient Response of Slep-Up
Regulator of Figure 11

A: Switch pin voltage, 10 VIdiv
S: Switch pin current, 2 A/div
c: Inductor current, 2 A/div
D: Output ripple voltage, 100 mV/div (AC·coupled)
Horizontal: 5 I's/dlv

A: Oulput Voltage Change, 100 mVIdiv. (AC-coupled)
S: Load current. 0.2 Aldiv
Horizontal: 5 ms/div

3-103

•

Application Hints (Continued)
FLYBACK REGULATOR
A Flyback regulator can produce single or multiple output
voltages that are lower or greater than the input supply voltage. Figure 15 shows the LM1577/LM2577 used as a flyback regulator with positive and negative regulated outputs.
Its operation is similar to a step-up regulator, except the
output switch contois the primary current of a flyback transformer. Note that the primary and secondary windings are
out of phase, so no current flows through secondary when
current flows through the primary. This allows the primary to
charge up the transformer core when the switch is on. When
the switch turns off, the core discharges by sending current
through the secondary, and this produces voltage at the
outputs. The output voltages are controlled by adjusting the
peak primary current, as described in the step-up regulator
section.
Voltage and current waveforms for this circuit are shown in
Figure 16, and formulas for calculating them are given in

Where l:ILOAO(max) is the sum of the load current (magnitude) required from both outputs. Select a resistor less than
or equal to this value, and no greater than 3 kn.
B. Calculate the minimum value for l:COUT (sum of COUT
at both outputs) using the following two equations.
COUT

~

_
0_.1_9_X_Rc'-c=-=-X_L...cp:-;X_l:_I.::LO",A",O",(",m=axl
15V x VIN(min)

and
V.!!.IN""(m""i",nlc....X_R....:c"-X_N.,..2_X-:-::,::(V:-"IN..!.l(,,,m,,,inL-l_+...:.(3_.7_4_X_10_5_X_L...!,p-,-,-ll
COUT~ _
487,800 X (15V)2X (15V + VIN(min) x N)
The larger of these two values must be used to ensure regulator stability.
VSW~Fr) - r-1-

SWITCH
VOLTAGE

SAT

ov - - - - - - - - - - - - -

~~ :[I==j--t==:

DIODE
VOLTAGE

Figure 17.

- -r-T - - _L _.L-I __ L-

vR -

FLYBACK REGULATOR DESIGN PROCEDURE

--

-

j
-iLL(]------ ---f'
alp(PK)

1_ Transformer Selection
A family of standardized flyback transformers is available for
creating flyback regulators that produce dual output voltages, from ± 1OV to ± 15V, as shown in Figure 15. Figure
18 lists these transformers with the input voltage, output
voltages and maximum load current they are designed for.

PRIMARY
CURRENT

DIODE
CURRENT

2. Compensation Network (Ce, Rc) and
Output Capacitor (COUT) Selection
As explained in the Step-Up Regulator DeSign Procedure,
Cc, Rc and COUT must be selected as a group. The following procedure is for a dual output flyback regulator with
equal turns ratios for each secondary (i.e., both output voltages have the same magnitude). The equations can be
used for a single output regulator by changing l:ILOAO(max)
to ILOAO(max) in the following equations.
A. First, calculate the maximum value for Rc.

ip(PKl

0-

--

----

Io(PK) -~---------

- -- - -----

Io~~-

0-

-

-

-TL/H/1146B-17

FIGURE 16. Flyback Regulator Waveforms

Rc ,,; -,-7.::..50"--X-=l:-",IL",O""A",O",,(m~a,,,xlLX--'(-,:15::-V,,--+---'.V.!.CIN~(m~i~nlLN2-)2
VIN(minl2
01

+VOUT

•

lop

-VOUT

5

4
Rl

SWITCH

F.B.

.I:

COUT

t - - - - -.....

LM2577-ADJ
R2

TL/H/1146B-1B

Tl = Pulse Engineering, PE-65300
01,02 = lN5821

FIGURE 15. LM1577-ADJ/LM2577-ADJ Flyback Regulator with ± Outputs
3-104

riii:
en

....

Application Hints (Continued)

......

Duty Cycle

VOUT + VF
::::
N (VIN - VSAT) + VOUT + VF
VOUT
N (VIN) + VOUT

D

......
......

riii:
en

I\)

......
......

alp

D (VIN - VSAT)
Lp x 52,000

en
CD
rn

Ip(PK)

N ~ILOAD
alpK
-x--+-'l'J
1- D
2

Switch Voltage
when Off

VSW(OFF)

V + VOUT + VF
IN
N

Diode Reverse
Voltage

VR

VOUT+ N (VIN- VSAT)

Average Diode
Current

ID(AVE)

ILOAD

Peak Diode
Current

ID(PK)

ILOAD + allND
1- D
2

Primary Current
Variation
Peak Primary
Current

6A
N

Short Circuit
Diode Current

::3.

CD

::::-

Power Dissipation
of LM1577/LM2577

0.250 (N

Po

1~~O;D

r

+

N ILOADD V
50 (1 - D) IN
N = Transformer Turns Ratio =

numb~ of :ec~ndary turns
nurn sr 0 primary turns

'I = Transformer Efficiency (typically 0.95)
l:ILOAC = 1+ ILOACI +!-iLOACI

FIGURE 17. Flyback Regulator Formulas
This formula can also be used to calculate the maximum
ESR of a single output regulator.
At this point, refer to this same section in the Step-Up Regulator Design Procedure for more information regarding
the selection of COUTo

C. Calculate the minimum value of Cc

Cc :<: _5B_.5_X_C-,O""U",T_X=-V'!f0",UT":-:-X-,(-,VO:<;U""T'-+-:-:-,(V-,I:!.!N",(m",,ln!L.)_X_N...:.:.))
, Rc2 x VIN(min) x N
D. Calculate the maximum ESR of the + VOUT and - VOUT
output capacitors in parallel.
ESR+IIESR_ s; B.7 x 10- 3 x VIN(min) x VOUT x N
~ILOAD(max) X (VOUT+ (VIN(min) x N))

•
3-105

o

CP
.;::

~

.....
.....
Ln
C"II
:::e
....I

".....

.....
Ln

....

:::e
....I

r-------------------------------------------------------------------------------~

Application Hints (Continued)
3. Output Voltage Selection
This section is for applications using the LM1577-AOJI
LM2577-ADJ. Skip this section if the LM1577-12/LM257712 or LM1577-15/LM2577-15 is being used.
With the LM1577-AOJ/LM2577-AOJ, the output voltage is
given by

back regulator generates more noise at the input supply
than a step-up regulator, and this requires a larger bypass
capaCitor to decouple the LM1577/LM2577 VIN pin from
this noise. For most applications, a low ESR, 1.0 ,.F cap will
be sufficient, if it is connected very close to the VIN and
Ground pins.
In addition to this bypass cap, a larger capacitor (;" 47 ,.F)
should be used where the flyback transformer connects to
the input supply. This will attenuate noise which may interfere with other circuits connected to the same input supply
voltage.
6. Snubber Circuit
A "snubber" circuit is required when operating from input
voltages greater than 10V, or when using a transformer with
Lp ;" 200 fLH. This circuit clamps a voltage spike from the
transformer primary that occurs immediately after the output
switch turns off. Without it, the switch voltage may exceed
the 65V maximum rating. As shown in Figure 19, the snubber consists of a fast recovery diode, and a parallel RC. The
RC values are selected for switch clamp voltage (VCLAMP)
that is 5V to 10V greater than VSW(OFF). Use the following
equations to calculate Rand C;

VOUT = 1.23V (1 + R1/R2)
Resistors R1 and R2 divide the output voltage down so it
can be compared with the LM1577-AOJ/LM2577-AOJ internal 1.23V reference. For a desired output voltage VOUT.
select R1 and R2 so that
R1
VOUT
R2 = 1.23V- 1
4. Diode Selection
The switching diode in a flyback converter must withstand
the reverse voltage specified by the following equation.
VIN
VR = VOUT+"N
A suitable diode must have a reverse voltage rating greater
than this. In addition it must be rated for more than the
average and peak diode currents listed in Figure 17.

C ;"

5. Input CapaCitor Selection
The primary of a flyback transformer draws discontinuous
pulses of current from the input supply. As a result, a flyTransformer
Type

1

2

3

Lp=100,.H
N=1

Lp = 200,.H
N = 0.5

Lp = 250,.H
N = 0.5

Input
Voltage

Dual
Output
Voltage

Maximum
Output
Current

5V
5V
5V

±10V
±12V
±15V

325mA
275mA
225mA

10V
10V
10V
12V
12V
12V

±10V
±12V
±15V
±10V
±12V
±15V

700mA
575mA
500mA
800mA
700mA
575mA

15V
15V
15V

±10V
±12V
±15V

900mA
825mA
700mA

0.02 x Lp X Ip(PK)2
(VCLAMP? - (VSW(OFF)2

R ,;; (VCLAMP + VSW(OFF) - VIN)2 X (19.2 X 10- 4 )
2
Lp X Ip(PK)2
Power dissipation (and power rating) of the resistor is;
p = (VCLAMP +

V~W(OFFl

- VIN

r

IR

The fast recovery diode must have a reverse voltage rating
greater than VCLAMP.
RC

SNUBBE~

~

l'

,Jllt

1..---41-1.14
..........

FAST RECOVERY DIODE

SWITCH

Manufacturers' Part Numbers

Transformer
Type

AlE

Pulse

Renco

1
2
3

326-0637
330-0202
330-0203

PE-65300
PE-65301
PE-65302

RL-2580
RL-2581
RL-2582

LM2577
TL/H/11468-19

FIGURE 19. Snubber Circuit

FIGURE 18. Flyback Transformer Selection Guide

3-106

Application Hints (Continued)
FLYBACK REGULATOR CIRCUIT EXAMPLE
The circuit of Figure 20 produces ± 15V (at 225 mA each)
from a single 5V input. The output regulation of this circuit is
shown in Figures 21 and 22, while the load transient response is shown in Figures 23 and 24. Switching waveforms
seen in this circuit are shown in Figure 25.
+VOUT
+15V@225mA
r~*-........- +--0
~ 470p.F
01

... r

J.----..
•
I ~_
T1
l:N

lp

[0
., •
I

*

.....I

J

OUT
C
-VOUT
-15V@225mA

02

' 1.....

~--~V·~~~-l+---~

'\,5

.r

4

2

COUT
470p.F

NOTE: PIN NUMBERS
SHOWN ARE FOR THE
TO-220 (T) PACKAGE.

L..C_C.....
I~_0._47_P._F_,

....
::>
a..
....
::>
0

- 60.11

15.220

15.1BO

~ 15.200

'"

15.1BO

0

15.160

....
::>
....a..
::>

15.140

'""'"
:;

""'\

>

15.0BO
15.0BO

0

\

\

\

15.120

15.040

15.100

15.020L...l.--'--'--"'_..l.--'--'---'-'
4.0 B.O B.O 10.0 12.0 14.0 1B.0 1B.0

15.0BOL...l.-'--...L---'--'--'--",_..J...J
4.0 6.0 B.O 10.0 12.0 14.0 16.0 1B.0

INPUT VOLTAGE (v)

INPUT VOLTAGE (v)
TL/H/1146B-22

TUH/1146B-21

FIGURE 22. Line Regulation (Typical) of Flyback
Regulator of Figure 20, -15V Output

FIGURE 21. Line Regulation (Typical) of Flyback
Regulator of Figure 20, + 15V Output

3-107

Application Hints

(Continued)

100mV
[

100mV

A

[

A

-100m:

-100m:

200mA

100mA

Bloom:

200mA

[

TL/H/l 1466-24

FIGURE 24. Load Transient Response of Flyback
Regulator of FIgure 20, -15V Output

TL/H/l 1468-23

FIGURE 23. Load Transient Response of Flyback
Regulator of FIgure 20, + 15V Output

A: Output Voltage Change, 100 mVIdiv
B: Output Current, 100 mAidiv
Horizontal: 10 ms/dlv

A: Output Voltage Change, 100 mVidiv
B: Output Current, lOa mAidiv
Horizontal: 10 ma/dlv

A

eo:

B{2:
( lA

cl °

DC

0
TL/H/11468-25

FIGURE 25. Switching Waveforms of Flyback Regulator of FIgure 20, Each Output Loaded with 60n
A: Switch pin voltage, 20 Vldiv
B: Primary current, 2 Aldlv
C: + 15V Secondary current, 1 A/div
D: + 15V Output ripple voltage, 100 mVIdiv

Horizontal: 51's/dlv

3-108

~National

~ Semiconductor

LM 1578A/LM2578A/LM3578A Switching Regulator
General Description

Features

The LM1578A is a switching regulator which can easily be
set up for such DC-to-DC voltage conversion circuits as the
buck, boost, and inverting configurations. The LM1578A
features a unique comparator input stage which not only
has separate pins for both the inverting and non-inverting
inputs, but also provides an internal 1.0V reference to each
input, thereby simplifying circuit design and p.c. board layout. The output can switch up to 750 rnA and has output
pins for its collector and emitter to promote design flexibility.
An external current limit terminal may be referenced to either the ground or the Vin terminal, depending upon the application. In addition, the LM1578A has an on board oscillator, which sets the switching frequency with a single external capacitor from < 1 Hz to 100 kHz (typical).
The LM1578A is an improved version of the LM1578, offering higher maximum ratings for the total supply voltage and
output transistor emitter and collector voltages.

•
•
•
•
•
•

Inverting and non-inverting feedback inputs
1.0V reference at inputs
Operates from supply voltages of 2V to 40V
Output current up to 750 rnA, saturation less than O.9V
Current limit and thermal shut down
Duty cycle up to 90%

Applications
• Switching regulators in buck, boost, inverting, and
single-ended transformer configurations
• Motor speed control
• Lamp flasher

Functional Diagram

TIMING CAPACITOR
PIN 3

3-109

GROUND
PIN 4
TL/H/8711-1

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Total Supply Voltage

Maximum Junction Temperature

-0.3Vto +50V

Emitter Output to Ground (Note 2)

-1Vto +50V

Power Dissipation (Note 3)

Internally limited

Output Current

750mA

Storage Temperature

- 65'C to + 150'C

Lead Temperature
(soldering, 10 seconds)

2kV

Operating Ratings

50V

Collector Output to Ground

150"C

ESD Tolerance (Note 4)

260'C

Ambient Temperature Range
LM1578A
LM2578A
LM3578A

-55'C:s; TA :S;+125'C
-40'C:s; TA :S;+85'C
O'C:S; TA:S; +70"C

Junction Temperature Range
LM1578A
LM2578A
LM3578A

-55'C:S; TJ :S;+150'C
-40'C:s; TJ :S;+125'C
O'C:s; TJ :S;+125'C

Electrical Characteristics

These specifications apply for 2V :s; VIN :s; 40V (2.2V :s; VIN :s; 40V for TJ :s; -25'C), timing capacitor Or = 3900 pF, and 25%
:s; duty cycle :s; 75%, unless otherwise specified. Values in standard typeface are for TJ = 25'C; values in boldface type apply
for operation over the specified operating junction temperature range.

Symbol

Parameter

Typical
(Note 5)

Conditions

LM1578A
Limit
(Notes 6,11)

LM2578A1
LM3578A
Limit
(Note 7)

22.4
17.6

24
16

Units

OSCILLATOR
fosc

Afosc/AT

Frequency

20

Frequency Drift with
Temperature
Amplitude

kHz
kHz (max)
kHz (min)

-0.13

%I'C

550

mVp_p

REFERENCE/COMPARATOR (Note 8)
VR

AVR/AVIN
IINV

Input Reference
Voltage

11 = 12 = OmAand
11 = 12 = 1 mA ±1% (Note 9)

1.0

Input Reference Voltage Line Regulation

11 = 12 = 0 mA and
11 = 12 = 1 mA ±1% (Note 9)

0.003

Inverting Input
Current

11 = 12 = 0 mA, duty cycle = 25%

Level Shift Accuracy

Level Shift Current

=

V

1.035/1.050 1.050/1.070 V (max)
0.965/0.950 0.95010.930 V (min)
0.01/0.02

1 mA

0.5
1.0

Input Reference
Voltage Long Term
Stability

%IV
%1V(max)

/JoA

5/8
AVR/At

0.01/0.02

10/13

100

%
% (max)
ppm/1000h

OUTPUT
Vc (sat)
VE (sat)
ICES
BVCEO(SUS)

Collector Saturation
Voltage

Ic = 750 mA pulsed, Emitter
grounded

0.7

Emitter Saturation
Voltage

10 = 80 mA pulsed,

1.4

VIN

Collector Leakage
Current

VIN
grounded, Output OFF

Collector-Emitter
Sustaining Voltage

ISUST

=
=

= 40V
VCE = 40V, Emitter

Vc

=

0.2A (pulsed), VIN

0.85/1.2

0.90/1.0

V
V (max)

1.6/2.1

1.712.0

V
V (max)

50/100

200/250

0.1

=

0

/JoA

60
50

3-110

50

IJ.A (max)

V
V (min)

Electrical Characteristics (Continued)
Symbol

Parameter

LM1578A

Typical

Conditions

LM2578A1
LM3578A

Limit

(Note 5)

Units

Limit

(Note 6)

(Note 7)

CURRENT LIMIT
VCl

l:..VCl/l:..T

Sense Voltage

Referred to VIN or Ground

Shutdown Level

(Note 10)

mV

110
95

80

mV(min)

140

160

mV(max)

0.3

%I'C

Referred to VIN

4.0

/LA

Referred to ground

0.4

/LA

Sense Voltage
Temperature Drift

ICl

Sense Bias Current

DEVICE POWER CONSUMPTION
Is

Supply Current

Output OFF, VE

=

OV

mA

2.0

3.5/4.0

3.013.3
Output ON, Ic
VE

=

=

750 mA pulsed,

mA(max)

14

mA

OV

Nole 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. DC and AC electrical specifications do not apply when operating
the device beyond its rated operating condttions.
Note 2: For TJ ;" 100·C, the Emitter pin voltage should not be driven more than 0.6V below ground (see Application Information).
Nole 3: At elevated temperatures, devices must be derated based on package thermal resistance. The device in the TO-99 package must be derated at 150·C/W,
junction to ambient, or 45·C/W, junction to case. The device in the 8·pln DIP must be derated at 95·C/W, junction to ambient. The device in the surface·mount
package must be derated at 150·C/W, junction·to·ambient.
Note 4: Human body model, 1.5 kG in series with 100 pF.
Note 5: Typical values are for TJ

= 25°C and represent the most likely parametric norm.

Note 6: All limits guaranteed and 100% production tested at room temperature (standard type face) and at temperature extremes (bold type face). All limits are
used to calculate Average Outgoing Quality Level (AOQL).
Note 7: All limits guaranteed at room temperature (standard type face) and at temperature extremes (bold type face). Room temperature limits are 100%
production tested. Limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods. All limits are used to
calculate AOQL.
Note 8: Input terminals are protected from accidental shorts to ground but jf external Yoltages higher than the reference voltage are applied, excessive current will
flow and should be limited to less than 5 mAo
Note 9: 11 and 12 are the external sink currents at the inputs (refer to Test Circuit).
Note 10: Connection of a 10 kG resistor from pin 1 to pin 4 will drive the duty cycle to its maximum, typically 90%. Applying the minimum Current Limit Sense
Voltage to pin 7 will not reduce the duty cycle to less than 50%. Applying the maximum Current Limit Sense Voltage to pin 7 is cerlain to reduce the duty cycle
below 50%. Increasing this voltage by 15 mV may be required to reduce the duty cycle to 0%, when the Collector output swing Is 40V or greater (see Ground·Referred Current Umit Sense Voltage typical curve).
Note 11: A military RETS specification is available on request. At the time of printing, the LM1578A RETS spec complied with the boldface limits in this column.
The LM1578AH may also be procured as a Standard Military Drawing.

Connection Diagram and Ordering Information
Metal Can

Dual-In-Line Package

VIN
-INPUT- 1
8
-INPUT

+ INPUT

1

7

2

+ INPUT-

CURRENT
LIMIT

6

2

'-../
8 r-VIN
7 r-CURRENT LIMIT

OSC- 3

6 r- COLLECTOR

GND- 4

5 r-EMITTER

COLLECTOR
TL/H/B711-29

OSC

5

3

Order Number LM3578AM, LM2578AN or LM3578AN
See NS Package Number M08A or N08E

EMITTER

4
GND
TL/H/B711-2B
Top View
Order Number LM1578AH, LM1578AH/883,
LM2578AH or LM3578AH
See NS Package Number H08C

3-111

•

Typical Performance Characteristics
Oscillator Frequency Change
with Temperature
1.3

800

1.2

750

1.1

1.0

r-- r--.~
...........

0.9

............

]:

700

!il
~

300

~

250

~

200

~

150

D.7
-50 -25 a

25 50 75 100 125 150

-r--

UPPER LIMIT

-

l.OJO
1.Q20

£
~
~

0.990

Z

0.980

Ij

~

..... f-

~

""i.OWER UMIT

1.000

......

~

1.010

-r--

~i"'"

-

......

0.970
0.960

Cr=4nr

100
-50 -25 a

TEMPERAlIJRE (OC)

0.81--+---'

i'..

0.950
25 50 75 100 125 150

-50 -25 a

lEMPERAlIJRE (OC)

Collector Saturation Voltage
(Sinking Current,
Emitter Grounded)
:!.

Input Reference Voltage
Drift with Temperature

Oscillator Voltage Swing

25 50 75 100 125 150

lEMPERAlIJRE (OC)

Emitter Saturation Voltage
(Sourcing Current,
Collector at Vin)

Ground Referred
Current Limit Sense Voltage

1.0 r---r---r-'--"'T.""--:--1

100

0.8r--+--+-~~r,~

80

D.6 I--t--+-:--It--Jf+---f--l

60

f=20kHz
C=4OV SWING
E=GROUND
INV INPUT=
10kA TO GND

0.41--t-0.2 I-~~~'---+-+---l

0.2

0.4

0.6

0.8

0.2 I--t--+f--+++-I--l

20

O'---'~01<1._--""'---"---'

a

o

1.0

COLLECTOR-EMITTER VOLTAGE (V)

D.4

0.8

1.2

1.6

2.0

Current Limit Sense Voltage
Drift with Temperature

120

~

100

COLLECTOR OUTPUT
SWING =15V
VINI=ly ••1.
GND REFERRED

~

~

 100 MO
Noto 3: 'LM1578 max duty cycle Is 90%

TL/H/8711-3

Definition of Terms
Input Reference Voltage: The voltage (referred to ground)
that must be applied to either the inverting or non-inverting
input to cause the regulator switch to change state (ON or
OFF).
Input Reference Current: The current that must be drawn
from either the inverting or non-inverting input to cause the
regulator switch to change state (ON or OFF).
Input Level Shift Accuracy: This specification determines
the output voltage tolerance of a regulator whose output
control depends on drawing equal currents from the inverting and non-inverting inputs (see the Inverting Regulator of
Figure 21, and the RS-232 Line Driver Power Supply of Figure2S).
Level Shift Accuracy is tested by using two equal-value resistors to draw current from the inverting and non-Inverting
input terminals, then measuring the percentage difference in
the voltages across the resistors that produces a controlled
duty cycle at the switch output.

Col/ector Saturation Voltage: With the inverting input terminal grounded thru a 10 kO resistor and the output transistor's emitter connected to ground, the Collector SaturationVoltage is the collector-to-emitter voltage for a given collector current.
Emitter Saturation Voltage: With the inverting input terminal grounded thru a 10 kO resistor and the output transistor's collector connected to Vln, the Emitter Saturation Voltage is the collector-to-emitter voltage for a given emitter
current.
Col/ector Emitter Sustaining Voltage: The collector-emitter breakdown voltage of the output transistor, measured at
a specified current.
Current Limit Sense Voltage: The voltage at the Current
Limit pin, referred to either the supply or the ground terminal, which (via logic circuitry) will cause the output transistor
to turn OFF and resets cycle-by-cycle at the oscillator frequency.

3-113

Ii:

I
r

a:

Co)

UI

~

OUTPUT TRANSISTOR
The output transistor is capable of delivering up to 750 mA
with a saturation voltage of less than 0.9V. (see Collector
Saturation Voltage and Emitter Saturation Voltage curves).
The emitter must not be pulled more than 1V below ground
(this limit is 0.6V for TJ ~ 100"C). Because of this limit, an
external transistor must be used to develop negative output
voltages (see the Inverting Regulator Typical Application).
Other configurations may need protection against violation
of this limit (see the Emitter Output section of the Applications Information).

Definition of Terms (Continued)
Current Limit Sense Current: The bias current for the Current Limit terminal with the applied voltage equal to the Current Limit Sense Voltage.
Supply Current: The IC power supply current, excluding the
current drawn through the output transistor, with the oscillator operating.
Functional Description
The LM157aA is a pulse-width modulator designed for use
as a switching regulator controller. It may also be used in
other applications which require controlled pulse-width voltage drive.
A control Signal, usually representing output voltage, fed
into the LMI57aA's comparator is compared with an internally-generated reference. The resulting error signal and the
oscillator's output are fed to a logic network which determines when the output transistor will be turned ON or OFF.
The follOwing is a brief description of the subsections of the
LMI57BA.

CURRENT LIMIT
The LMI57aA's current limit may be referenced to either
the ground or the Vin pins, and operates on a cycle-by-cycle
basis.
The current limit section consists of two comparators: one
with its non-inverting input referenced to a voltage 110 mV
below Vin, the other with its inverting input referenced
110 mV above ground (see FUNCTIONAL DIAGRAM). The
current limit is activated whenever the current limit terminal
is pulled 110 mV away from either Vin or ground.

COMPARATOR INPUT STAGE
The LMI57BA's comparator input stage is unique in that
both the inverting and non-inverting inputs are available to
the user, and both contain a 1.0V reference. This is accomplished as follows: A 1.0V reference is fed into a modified
voltage follower circuit (see FUNCTIONAL DIAGRAM).
When both input pins are open, no current flows through Rl
and R2. Thus, both inputs to the comparator will have the
potential of the 1.0V reference, VA. When one input, for
example the non-inverting input, is pulled aV away from VA,
a current of aV/Rl will flow through Rl. This same current
flows through R2, and the comparator sees a total voltage
of 2aV between its inputs. The high gain of the system,
through feedback, will correct for this imbalance and return
both inputs to the 1.0V level.

Applications Information
CURRENT LIMIT
As mentioned in the functional description, the current limit
terminal may be referenced to either the Vin or the ground
terminal. Resistor R3 converts the current to be sensed into
a voltage for current limit detection.
VIN

Lt.t1578A

This unusual comparator input stage increases circuit flexibility, while minimizing the total number of external components required for a voltage regulator system. The inverting
switching regulator configuration, for example, can be set up
without having to use an external op amp for feedback polarity reversal (see TYPICAL APPLICATIONS).
OSCILLATOR
The LM157BA provides an on-board oscillator which can be
adjusted up to 100 kHz. Its frequency is set by a single
external capacitor, C1 , as shown in Figure 1, and follows the
equation
fose = aXl0- 5/Cl

TL/H/B711-15

FIGURE 2. Current Limit, Ground Referred
VIN

The oscillator provides a blanking pulse to limit maximum
duty cycle to 90%, and a reset pulse to the internal circuitry.
Lt.t1578A

l00~.
~

10

111'IJJ11

5

11111111

li!

§I.oMM_
5

FREQUEIICY (kHz)

TL/H/B711-18

FIGURE 3. Current Limit, Vln Referred

TL/H/B711-4

FIGURE 1. Value of Timing CapaCitor vs
OSCillator Frequency
3-114

Applications Information

.i:
....
CII

(Continued)

CURRENT LIMIT TRANSIENT SUPPRESSION
When noise spikes and switching transients interfere with
proper current limit operation, R1 and C1 act together as a
low pass filter to control the current limit circuitry's response
time.

.....

VIN

CD

l>
....,.

8

2

Because the sense current of the current limit terminal varies according to where it is referenced, R1 should be less
than 2 kn when referenced to ground, and less than 100n
when referenced to Vin.

3

.-i:

R2

N

CII
.....
CD

7
Lt.t1578A

.....-l>

6

Rl

5

i:
w
CII
.....
CD

l>

TUH/8711-20

FIGURE 7. Current limit Sense Voltage Multiplication,
Vln Referred

2

3

Lt.t1578A

UNDER-VOLTAGE LOCKOUT
Under-voltage lockout is accomplished with few external
components. When Vin becomes lower than the zener
breakdown voltage, the output transistor is turned off. This
occurs because diode D1 will then become forward biased,
allowing resistor R3 to sink a greater current from the noninverting input than is sunk by the parallel combination of R1
and R2 at the inverting terminal. R3 should be one-fifth of
the value of R1 and R2 in parallel.

4

TUH/8711-17

FIGURE 4. Current limit Transient Suppressor,
Ground Referred
VIN

2

3

Lt.t1578A
Lt.t1578A

Rl

5

4

TUH/8711-18

FIGURE 5. Current Limit Transient Suppressor,
Vln Referred

TUH/8711-22

FIGURE 8. Under-Voltage Lockout

C.L SENSE VOLTAGE MULTIPLICATION

MAXIMUM DUTY CYCLE LIMITING
The maximum duty cycle can be externally limited by adjusting the charge to discharge ratio of the oscillator capacitor
with a single external resistor. Typical values are 50 /LA for
the charge current, 450 /LA for the discharge current, and a
voltage swing from 200 mV to 750 mV. Therefore, R1 is
selected for the desired charging and discharging slopes
and C1 is readjusted to set the oscillator frequency.

When a larger sense resistor value is desired, the voltage
divider network, consisting of R1 and R2, may be used. This
effectively multiplies the sense voltage by (1 + R1/R2).
Also, R1 can be replaced by a diode to increase current limit
sense voltage to about 800 mV (diode Vj + 110 mV).
VIN

8
2

3
4

7

Lt.t1578A

6
5
R2

TUH/8711-19

FIGURE 6. Current Limit Sense Voltage Multiplication,
Ground Referred
3-115

Applications Information (Continued)

Rl
8

8

7
LM1578A

LM1578A

5

TL/H/8711-21

FIGURE 9. Maximum Duty Cycle Limiting
DUTY CYCLE ADJUSTMENT
When manual or mechanical selection of the output transistor's duty cycle Is needed, the ciruclt shown below may be
used. The output will turn on with the beginning of each
oscillator cycle and turn off when the current sunk by R2
and RS from the non-Inverting terminal becomes greater
than the current sunk from the Inverting terminal.
With the resistor values as shown, RS can be used to adjust
the duty cycle from 0% to 90%.
When the sum of R2 and RS Is twice the value of R1, the
duty cycle will be about 50%. C1 may be a large electrolytic
capacitor to lower the oscillator frequency below 1 Hz.

TLlH/8711-24

FIGURE 11. Shutdown Occurs when VL Is High
EMITTER OUTPUT
When the LM1578A output transistor Is in the OFF state, If
the Emitter output swings below the ground pin voltage, the
output transistor will turn ON because Its base Is clamped
near ground. The Col/ector Current with Emitter Output 8elow Ground curve shows the amount of Collector current
drawn In this mode, vs temperature and Emitter voltage.
When the Coliector-Emitter voltage Is high, this current will
cause high power dissipation in the output transistor and
should be avoided.
This situation can occur In the high-current high-voltage
buck application If the Emitter output Is used and the catch
diode's forward voltage drop Is greater than 0.8V. A fast-recovery diode can be added in series with the Emitter output
to counter the forward voltage drop of the catch diode (see
Figure 2). For better efficiency of a high output current buck
regulator, an external PNP transistor should be used as
shown In Figure 16.

Y,N

7
LM1578A

6
5

TL/H/8711-23

2

FIGURE 10. Duty Cycle Adjustment

3

.

REMOTE SHUTDOWN
The LM1578A may be remotely shutdown by sinking a
greater current from the non-inverting input than from the
Inverting input. This may be accomplished by selecting resistor RS to be approximately one-half the value of R1 and
R2 In paraliel.

TL/H/8711-30

FIGURE 12. D1 Prevents Output Transistor from
Improperly Turning ON due to D2's Forward Voltage

S-118

Applications Information

Component values are selected as follows:

(Continued)

Rl = (Vo - 1) x R2 where R2
R3 = VIIsw(max)
R3 = 0.150

SYNCHRONIZING DEVICES
When several devices are to be operated at once, their oscillators may be synchronized by the application of an external signal. This drive signal should be a pulse waveform with
a minimum pulse width of 2 IJ.s. and an amplitude from 1.5V
to 2.0V. The signal source must be capable of 1.) driving
capacitive loads and 2.) delivering up to 500 IJ.A for each
LM1578A.

where:
V is the current limit sense voltage, 0.11 V
Isw(max) is the maximum allowable current thru the output transistor.
L1 is the inductor and may be found from the inductance
calculation chart (Figure 16) as follows:

Capacitors Cl thru CN are to be selected for a 20% slower
frequency than the synchronization frequency.

Llot1578A

Given Vin = 15V
Vo = 5V
lo(max) = 350 mA fosc = 50 kHz
Discontinuous at 20% of lo(max).
Note that since the circuit will become discontinuous at
20% of lo(max), the load current must not be allowed to fall
below 70 mA.

Llot1578A - - - - - LM1578A

ALL DIODES ARE 1N914

1.5V

Dl

~~JLJl
~

-

Step 1: Calculate the maximum DC current through the inductor, IL(max). The necessary equations are indicated at
the top of the chart and show that IL(max) = lo(max) for the
buck configuration. Thus, IL(max) = 350 mAo
Step 2: Calculate the inductor Volts-sec product, E-Top , according to the equations given from the chart. For the Buck:

DN

o--4-------4--------~

2 1".
(min.)

E-Top = (Vin - Yo) (VoNin) (1000/fosc)
= (15 - 5) (5/15) (1000/50)

TL/H/6711-25

FIGURE 13. Synchronizing Devices

= 66V-lJ.s.
with the oscillator frequency, fose, expressed in kHz.

Typical Applications
The LM1578A may be operated in either the continuous or
the discontinuous conduction mode. The following applications (except for the Buck-Boost Regulator) are designed
for continuous conduction operation. That is, the inductor
current is not allowed to fall to zero. This mode of operation
has higher efficiency and lower EMI characteristics than the
discontinuous mode.

Vin = 15V
Vo = 5V
Vrippio = 10 mV
10 = 350 rnA
lose = 50 kHz
Rl = 40 kO
R2 = 10 kO
R3 = 0.150
Cl = 1820 pF
C2 = 220 p.F

BUCK REGULATOR
The buck configuration is used to step an input voltage
down to a lower level. Transistor 01 in Figure 14 chops the
input DC voltage into a squarewave. This squarewave is
then converted back into a DC voltage of lower magnitude
by the low pass filter consisting of L1 and Cl. The duty
cycle, D, of the squarewave relates the output voltage to the
input voltage by the following equation:
Vout = D X Yin = Yin X (Ion)/(ton

= 10 kO

C3
L1
01

= 20pF
= 470 p.H
= lN5818

TUH/6711-6

FIGURE 15. Buck or Step-Down Regulator
Step 3: Using the graph with axis labeled "Discontinuous At
% lOUT" and "IL(max, DC)" find the point where the desired
maximum inductor current, IL(max, DC) intercepts the desired
discontinuity percentage.
In this example, the point of interest is where the 0.35A line
intersects with the 20% line. This is nearly the midpoint of
the horizontal axis.
Step 4: This last step is merely the translation of the point
found in Step 3 to the graph directly below it. This is accomplished by moving straight down the page to the point which
intercepts the desired E-Top. For this example, E-Top is
66V-lJ.s and the desired inductor value is 470 IJ.H. Since this
example was for 20% discontinuity, the bottom chart could
have been used directly, as noted in step 3 of the chart
instructions.

+ told.

TL/H/6711-5

FIGURE 14. Basic Buck Regulator
Figure 15 is a 15V to 5V buck regulator with an output current, 10 , of 350 mA. The circuit becomes discontinuous at
20% of lo(max), has 10 mV of output voltage ripple, an efficiency of 75%, a load regulation of 30 mV (70 mA to
350 mAl and a line regulation of 10 mV (12 :5: Yin :5: 18V).

3-117

LM 1578A/LM2578A/LM3578A

~

HOW TO USE THIS CHART

, 

"C

"2..

[-TOp

,f

m

D.01A

REQUIRED "
DISCONTINUITY
AIL' 100"
= 21L, MAX DC
HERE
IF "20"" PROCEED
TOQ)

O·
j
(I)

---+-+

'§

5

a

.£>

:::l

c:
m

@ PROCEED --+

S

HORIZONTALLY TO
IL,MAX DC
FROM

~
~

co

. and 11V is the
peak-la-peak output voltage ripple. A larger output capaCitor
than this theoretical value should be used since electrolytics
have poor high frequency performance. Experience has
shown that a value from 5 to 10 times the calculated value
should be used.

For good efficiency. the diodes must have a low forward
voltage drop and be fast switching. 1N5819 Schottky diodes
work well.
Transformer selection should be picked for an output transistor "on" time of 0.4/f08c • and a primary inductance high
enough to prevent the outpul transistor switch from ramping
higher than the transistor's rating of 750 mA. Pulse Engineering (San Diego. Calif.) and Renco Electronics. Inc.
(Deer Park. N.Y.) can provide further assistance in selecting
the proper transformer for a specific application need. The
transformer used in Figure 23 was a Pulse Engineering
PE-64287.

3-122

r-------------------------------------------------------------------------,r
==

~National

...Cit

en

~ Semiconductor

C)

LM78S40
Universal Switching Regulator Subsystem
General Description

Features

The LM78S40 is a monolithic regulator subsystem consisting of all the active building blocks necessary for switching
regulator systems. The device consists of a temperature
compensated voltage reference, a duty-cycle controllable
oscillator with an active current limit circuit, an error amplifier, high current, high voltage output switch, a power diode
and an uncommitted operational amplifier. The device can
drive external NPN or PNP transistors when currents in excess of 1.5A or voltages in excess of 40V are required. The
device can be used for step-down, step-up or inverting
switching regulators as well as for series pass regulators. It
features wide supply voltage range, low standby power dissipation, high efficiency and low drift. It is useful for any
stand-alone, low part count switching system and works extremely well in battery operated systems.

•
•
•
•
•
•
•
•

Step-up, step-down or inverting switching regulators
Output adjustable from 1.25V to 40V
Peak currents to 1.5A without external transistors
Operation from 2.5V to 40V input
Low standby current drain
80 dB line and load regulation
High gain, high current, independent op amp
Pulse width modulation with no double pulsing

Block and Connection Diagrams
COMPARATOR
+IN

COMPARATOR
-IN

TIMING
CAPACITOR

DRIVER
SWITCH
COLLECTOR COLLECTOR

16-LeadDIP
DIODE
CATHODE

15

gtT~L'bOR
~l~~~TOR

14

IpK SENSE

16

DIODE
ANOOE
SWITCH
[MITTER

OP AIIP OUT
OP AMP
SUPPLY

13

VIN

12

TilliNG CAPACITOR

10

COMPARATOR -IN

9

COMPARATOR +IN

OP AUP +IH

OP AMP -IN
REFERENCE
VOLTAGE

Dl

REFERENCE
VOLTAGE

OP AMP
-IN

OP AMP
+IN

OP AMP
SUPPLY

OP AMP
OUT

----n--

SWITCH
EMmER

DIODE
ANODE

DIODE
CATHODE

TUH/l0057-2

Ordering Information
Part Number

NSPackage

Temperature Range

LM78S40J
LM78S40J/883

J16A Ceramic DIP
J16A Ceramic DIP

-55·Cto + 125·C

LM78S40N

N16E Molded DIP

-40·C to + 125·C

LM78S40CJ
LM78S40CN

J16A Ceramic DIP
N16E Molded DIP

O·Cto +70"C

3-123

TLlH/l0057-1

Top View

•

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Storage Temperature Range
-65·Cto + 175·C
Ceramic DIP
-65·Cto + 150'C
Molded DIP
Operating Temperature Range
Extended (LM7BS40J)
- 55·C to +125·C
Industrial (LM7BS40N)
-40·C to + 125·C
Commercial (LM7BS40CN)
O·Cto +70·C
Lead Temperature
Ceramic DiP (Soldering, 60 sec.)
300·C
Molded DIP (Soldering, 10 sec.)
2B5·C
Internal Power Dissipation (Notes 1, 2)
16L-Ceramlc DIP
1.50W
16L-Molded DIP
1.04W
Input Voltage from VIN to GND
40V
Input Voltage from V + (Op Amp) to GND
40V

Common Mode Input Range
(Comparator and Op Amp)
Differential Input Voltage
(Note 3)
Output Short Circuit
Duration (Op Amp)
Current from VREF
Voltage from Switch
Collectors to GND
Voltage from Switch
Emitters to GND
Voltage from Switch
Collectors to Emitter
Voltage from Power Diode to GND
Reverse Power Diode Voltage
Current through Power Switch
Current through Power Diode
ESD Susceptibility

-0.3toV+
±30V
Continuous
10mA
40V
40V
40V
40V
40V
1.5A
1.5A
(to be determined)

LM78S40
Electrical Characteristics
TA

= Operating temperature range, VIN = 5.0V, V+(Op Amp) = 5.0V, unless otherwise specified. (Note 4)

Symbol

I

Parameter

GENERAL CHARACTERISTICS
Icc
ICC

Supply Current
(Op Amp Disconnected)
Supply Current
(Op Amp Connected)

I

Conditions

I Min I Typ I Max I Units

= 5.0V
= 40V
VIN = 5.0V
VIN = 40V
VIN

1.B

3.5

rnA

VIN

2.3

5.0

rnA

4.0

rnA

5.5

rnA

1.245

1.310

V

REFERENCE SECTION
VREF

Reference Voltage

IREF

= 1.0mA

Extend - 55·C < TA < + 125·C,
CommO 1.216

25 so 75 100 125

JUNCTION TEMPERATURE - "C

OI'f'TIME-1'S

TLlH/l 0057-7

TL/H/l0057-8

Discharge Current vs
Input Voltage
250

Current Limit Sense
Voltage vs Input Voltage
400

/

_TA=25"C

""'l

I- TA=25"C
>350

./

I

>-

I8200

I

I::

~

'"

::1300

'"

~
0:

""u'"
fIJ

---

E

",

!z
t!
0:

l-

8250

Q

ISO

200
0

10

20

40

30

so

0

INPUT VOLTAGE - V

10

20

30

40

so

INPUT VOLTAGE - V
TL/H/I 0057-8

TLlH/l0057-9

Design Formulas
Characteristic

Step-Down

Step-Up

Inverting

ton

Vo + Vo

Vo + Vo - VI

Ivol + Vo

toft

VI- VSAT - Vo

VI- VSAT

VI- VSAT

1

1

(ton

+ toff) Max

-IMin

CT

4X10- 5 t on

IPk

2 lOMax

-

-

IMin

o Max

",,5

IMIN

4 X 10- 5 t on
21

1

Units

• ton + toft
toft

4 X 10- 5 ton
21

o Max

.ton+ton
toff

""F
A

LMin

(VI- VSAT- Vo)
I
ton Max
pk

(VI- VSAT)
I
ton Max
pk

(VI- VSAT)
I
ton Max
pk

""H

RSC

0.33/1 pk

0.33/1 pk

0.33/1 pk

n

Co

Ipk (ton + toff)

::::~·ton

""F

8 Vripple
Note: VSfooT

Vo

~

10

: : : : - - · ton
Vripple

Saturation voltage of the switching element
FolWllJ'd voltage of the flyback diode.

~

3-126

Vripple

Functional Description

Typical Applications

SWITCHING FREQUENCY CONTROL

VI
25V

The LM78S40 is a variable frequency, variable duty cycle
device. The initial switching frequency is set by the timing
capacitor. (Oscillator frequency is set by a single external
capacitor and may be varied over a range of 100 Hz to
100 kHz). The initial duty cycle is 6:1. This switching frequency and duty cycle can be modified by two mechanisms-the current limit circuitry (Ipk sense) and the comparator.
The comparator modifies the OFF time. When the output
voltage is correct, the comparator output is in the HIGH
state and has no effect on the circuit operation. If the output
voltage is too high then the comparator output goes LOW.
In the LOW state the comparator inhibits the turn-on of the
output stage switching transistors. As long as the comparator is LOW the system is in OFF time. As the output current
rises the OFF time decreases. As the output current nears
its maximum the OFF time approaches its minimum value.
The comparator can inhibit several ON cycles, one ON cycle or any portion of an ON cycle. Once the ON cycle has
begun the comparator cannot inhibit until the beginning of
the next ON cycle.

Rsc
0.33.0.

c,-

0.01 pF
VIN

__~
: ___L

The current limit modifies the ON time. The current limit is
activated when a 300 mV potential appears between lead
13 (Vcc) and lead 14 (Ipkl. This potential is intended to result when designed for peak current flows through Rse.
When the peak current is reached the current limit is turned
on. The current limit cirCUitry provides for a quick end to ON
time and the immediate start of OFF time.

=__ _

r±

'BIAS

Vo
10V
L
300!-,H

Rl

R2

Generally the oscillator is free running but the current limit
action tends to reset the timing cycle.
Increasing load results in more current limited ON time and
less OFF time. The switching frequency increases with load
current.

8Sk.o.

12k.o.

TLlH/100S7-3

FIGURE 1. Typical Step-Down Regulator and
Operational Performance (TA = 25°C)

USING THE INTERNAL REFERENCE, DIODE, AND
SWITCH

Condition

Characteristic

The internal 1.24SV reference (pin 8) must be bypassed,
with 0.1 p.F directly to the ground pin (pin 11) of the
LM78S40, to assure its stability.
VFD is the forward voltage drop across the internal power
diode. It is listed on the data sheet as 1.2SV typical, 1.SV
maximum. If an external diode is used, then its own forward
voltage drop must be used for VFD.
VSAT is the voltage across the switch element (output transistors 01 and 02) when the switch is closed or ON. This is
listed on the data sheet as Output Saturation Voltage.

Output Voltage

10

Line Regulation

20V,,; VI"; 30V

1.SmV

Load Regulation

S.OmA"; 10
10"; 300mA

3.0mV

Max Output Current

Vo

Output Ripple
Efficiency

"Output saturation voltage 1" is defined as the switching
element voltage for 02 and 01 in the Darlington configuration with collectors tied together. This applies to Figure 1,
the step down mode.
"Output saturation voltage 2" is the switching element voltage for 01 only when used as a transistor switch. This applies to Figure 2, the step up mode.
For the inverting mode, Figure 3, the saturation voltage of
the external transistor should be used for VSAT.

Standby Current
Nota k For 10
tion.

3-127

=

Typical
Value

~

200mA

= 9.SV
10 = 200mA
10 = 200mA
10 = 200mA

10V

SOOmA
SOmV
74%
2.8mA

200 rnA use external diode to limit on-chip power dlssipa..

C) r-------------------------------------------------------------------------------~

i.....

Typical Applications

:J

(Continued)
L

RSC

_ _...n"IM......
2NS003

300~H

0.334

c,0.01 J.lF

VIN

_~

VI

180.0.

RSC

12V

G__ _

0.334
02

___

n01

Vo
2SV
Rl

R2

12k.o.

230k.o.

Co

1500~F

112 k4

Vo
-ISV

TL/H/l00S7-4

FIGURE 2. Typical Step-Up Regulator and
Operational Performance (TA = 2S'C)

TUH/l00S7-S

FIGURE 3. Typical Inverting Regulator and
Operational Performance (TA = 2SOC)
Characteristic

Condition

Typical
Value

Characteristic

Condition

Typical
Value

Output Voltage

10 = SOmA

2SV

Output Voltage

10 = 100mA

Line Regulation

S.OV ,;;; VI';;; 1SV

4.0mV

Line Regulation

8.0V ,;;; VI ,;;; 18V

S.OmV

Load Regulation

S.OmA';;; '0
10';;; 100mA

2.0mV

Load Regulation

S.OmA';;; '0
'0';;; 1S0mA

3.0mV

Max Output Current

Vo = 23.7SV

160mA

Max Output Current

Vo = 14.2SV

160mA

Output Ripple

10 = SOmA

30mV

Output Ripple

10 = 100mA

20mV

Efficiency

10 = 100mA

70%

Standby Current

10 = 100mA

2.3mA

Efficiency

10 = SOmA

79%

Standby Current

10=SOmA

2.6mA

3-128

-1SV

,-----------------------------------------------------------------------------, r
:!:

Typical Applications (Continued)

ex:

!f

100l'H

2N60S1

r----9--".,.,...~...,

30VIN--.-----------.-------~~~~~~~~~_,

180n

Q

0.0041"

MBR4030
SHOTTKY

DI

----W--

B.2 kn

. ; 1.01"

0.021"

...-_;.;w,..;;...._'4--------------------.....--.... S.oA
s.ov
1.3kn

TLlH/l0057-10

FIGURE 4. Pulse Width Modulated Step-Down Regulator (fose

3·129

=

20 kHz)

~

~ ~National
..I

~ SemlconduclDr

LMC7660 Switched Capacitor Voltage Converter
General Description

Features

The LMC7660 is a CMOS voltage converter capable of converting a positive voltage in the range of + 1.SV to + 10V to
the corresponding negative voltage of -1.SV to -1 OV. The
LMC7660 is a pin-for-pin replacement for the industry-standard 7660. The converter features: operation over full temperature and voltage range without need for an external diode, low quiescent current, and high power efficiency.

• Operation over full temperature and voltage
range without an external diode
• Low supply current, 200 p.A max
• Pin-for-pin replacement for the 7660
• Wide operating range 1.SV to 10V
• 97% Voltage Conversion Efficiency
• 9S% Power Conversion Efficiency
• Easy to use, only 2 external components
• Extended temperature range

The LMC7660 uses its built-in oscillator to switch 4 power
MOS switches and charge two inexpensive electrolytic capaCitors.

Block Diagram

TUH/9136-1

Pin Configuration

Ordering Information
LMC7660MJ - S5°C :S: TA :S: + 125°C

LMC7660

N/COBv+

Cap+ 2
Gnd 3

Cap- 4

LMC7660IN -40"C :S: TA :S: +8SoC

7 Ose
6 LV

Vou!
TUH/9136-2

3-130

Absolute Maximum Ratings (Nole 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage
10.5V
Input Voltage on Pin 6, 7
(Note 2)

Package
Power Dissipation
(Note 3)

Current into Pin 6 (Note 2)

Bja (Note 3)
Storage Temp. Range

150"C

150·C

90·C/W

-65·C';;; T,;;; 150·C
260·C

Lead Temp.
(Soldering, 5 sec)
ESD Tolerance (Note 8)

20/LA

Output Short Circuit Duration
(V+ ,;;; 5.5V)

1.4W

140·C/W

Tj Max (Note 3)
-0.3V to (V+ + 0.3V)
for V+ < 5.5V
(V+ - 5.5V) to (V+ + 0.3V)
forV+ > 5.5V

N

J
0.9W

260"C
±2000V

Continuous

Electrical Characteristics (Note 4)
LMC7660MJ
Symbol
Is

Parameter
Supply Current

Conditions
RL

=

Typ

co

120

Tested
Limit
(NoteS)
200

400

LMC7660lN
Tested
Limit
(Note 5)

Design
limit
(Note 6)

200

400

Units
Limits

p.A
max

V+H

Supply Voltage
Range High (Note 7)

RL = 10 kO, Pin 6 Open
Voltage Efficiency:2: 90%

3to 10

31010

3to 10

31010

V

V+L

Supply Voltage
Range Low

RL = 10 kO, Pin 6 to Gnd.
Voltage Efficiency :2: 90%

1.5103.5

1.5103.5

1.5 to 3.5

1.5103.5

V

Rout

Output Source
Resistance

IL

100

120

0
max

200

300

0
max

=

20mA

55

V = 2V, IL = 3 mA
Pin 6 Short to Gnd.
Fosc

Oscillator
Frequency

Pelf

Power Efficiency

110

100

150
200

300

10
RL

=

97

5kO

kHz
95

90
Voelf

Voltage Conversion
Efficiency

RL

=

co

99.9

97

95

95

90

%
min

97

95

%
min

Pin 7 = Gnd. or V+
Oscillator Sink or
3
p.A
Source Current
Not. 1: Abselute Maximum ratings indicate limits beyond which damage to the device may occur. DC and AC electricalspecHications do not apply when operating
the device beyond its rated operating conditions. See Note 4 for conditions.
Not. 2: Connecting any input terminal to voltages greater than V+or less than ground may cause destructive latchup. It is recommended that no inputs from
seurces operating from external supplies be applied prior to "power-up" of the LMC766C.
Note 3: For operation at elevated temperature, these devices must be derated based on a thermal resistance of 6ja and Tj max, TJ = TA + 6ja PoNot. 4: Boldface numbers apply at temperature extremes. All other numbers apply at TA = 25"C, V+ = 5V, Cose = 0, and apply for the LMC7660 unless

losc

otherwise specified. Test circuit is shown in Figure 1.

Note 5: Guaranteed and 100% production tested.
Not. 6: Guaranteed over the operating temperature range (but not 100% tested). These limits are not used to calculate outgOing quaJIly levels.
Not. 7: The LMC7660 can operate without an external diode over the full temperature and voltage range. The LMC7660 can a1se be used with the external diode

Dx, when replacing previous 7660 designs.
Not. 8: The test circuit consists of the human body model of 100 pF in series with 15000.

3-131

•

C)

CD

r-------------------------------------------------------------------------------------,

5

:I

H/C

8

1
2
LMC7660

......_ _ _ _ _ _...._ Vout
C (-5v)
r~10J.lr
TUH/9136-5

FIGURE 1. LMC7660 Test Circuit

Typical Performance Characteristics
osc Freq. vs OSC
Capacitance

105

YoutVS lout@Y+ = 2Y

Yout VB lout @Y+ = 5Y

3

5
I
I
I

1

-

1

~~

-2

-

1

~

-2
-3

-4
-5
o

LOAD CURRENT (mA)

Supply Current & Power Efficiency
vs Load Current (Y+ = 2V)

r"""

90

.....

80

20
18
16
14
12
10

II'

I'"" I"'-. '/'~
1/

70

60
50
~

V

30
20
10

o II'

V

V

V

8
6
4

V

Supply Current & Power Efficiency
vs Load Current (Y+ = 5V)
100

90

l!!

=II

g

I I
!:(

8

!

0

0123458789

i

,.....

~

70

20

60
50

/
o 1/
o

16
14
12

\

"-

10

30

~

0

"0

'" i'-.. ["..

25

50

75 100 125

T£MPERATURE (OC)

i

10'1

~

50

80

300

50

60

v+=2V

o

Output R va Supply Yoltage

I--

-50 -25

v+=5V
101ll=20mA

0

25

50

75 100 125

T£MPERATURE (OC)

Pefl VB OSC Freq. @Y+ = 5Y
100

LV OPEN

~
J.-

-

I ': -

LOAD CURRENT (mA)

LV TO ~
GROUND

6

-50 -25

::1 !
20

10

30

LOAD ClJRRENT (mA)

Output Source Resistance as a
Function of Temperature

: i I:

/
1/

30
20
10

50
80

-

l!! '"
70;ae2S0

/

~

~

18

/-

,/

LOAO ClJRRENT (mA)

Unloaded Oscillator Frequency
as a Function of Temperature

... :.......

20

10

/

350

100

80

-

~

012345678

100

•
•

1

98
96
94
92
90
B8
86

1111

II 111111

1111

II IllIn",
II

Cp=Cr =1 0/-11

111111

1~I=ri

,'Ou1~\

mA

84
82

TA=25OC

10
012345678
SUPPLY VOLTAGE ('t)

60 ,02
OSCILLATOR FREQUENCY (Hz)
TL/H/9136-4

3·132

The LMC7660 closely approaches 1 and 2 above. By using
a large pump capacitor Cp, the charge removed while supplying the reservoir capacitor is small compared to Cp's total
charge. 8mall removed charge means small changes in the
pump capacitor voltage, and thus small energy loss and
high efficiency. The energy loss by Cp is:
E = Y.C p (V1 2 - V22)
By using a large reservoir capacitor, the output ripple can be
reduced to an acceptable level. For example, if the load
current is 5 mA and the accepted ripple is 200 mV, then the
reservoir capacitor can omit approximately be calculated
from:

CIRCUIT DESCRIPTION
The LMC7660 contains four large CM08 switches which
are switched in a sequence to provide supply inversion YOU!
= - Yin. Energy transfer and storage are provided by two
inexpensive electrolytic capacitors. Figure 2 shows how the
LMC7660 can be used to generate -V+ from V+. When
switches 81 and 83 are closed, Cp charges to the supply
voltage V+. During this time interval, switches 82 and 84
are open. After Cp charges to V+, 81 and 83 are opened,
82 and 84 are then closed. By connecting 82 to ground, Cp
develops a voltage - V+ 12 on Cr. After a number of cycles
Cr will be pumped to exactly -V+. This transfer will be
exact assuming no load on Cn and no loss in the switches.
In the circuit of Figure 2, 81 is a P-channel device and 82,
83, and 84 are N-channel devices. Because the output is
biased below ground, it is important that the p- wells of 83
and 84 never become forward biased with respect to either
their sources or drains. A substrate logic circuit guarantees
that these p- wells are always held at the proper voltage.
Under all conditions 84 p- well must be at the lowest potential in the circuit. To switch off 84, a level translator generates VGS4 = OV, and this is accomplished by biasing the
level translator from the 84 p- well.

dv
Is = Cr"dt

-

0.5mA
Cr = 0.5V/ms = 10,..F

1) Do not exceed the maximum supply voltage or junction
temperature.
2) Do not short pin 6 (LV terminal) to ground for supply voltages greater than 3.5V.
3) Do not short circuit the output to V+.
4) External electrolytic capacitors Cr and Cp should have
their polarities connected as shown in Figure 1.
REPLACING PREVIOUS 7660 DESIGNS
To prevent destructive latchup, previous 7660 deSigns require a diode in series with the output when operated at
elevated temperature or supply voltage. Although this prevented the latchup problem of these designs, it lowered the
available output voltage and increased the output series resistance.
The National LMC7660 has been designed to solve the inherent latch problem. The LCM7660 can operate over the

POWER EFFICIENCY AND RIPPLE
It is theoretically possible to approach 100% efficiency if the
following conditions are met:
1) The drive circuitry consumes little power.
2) The power switches are matched and have low Ron.
3) The impedance of the reservoir and pump capacitors are
negligibly small at the pumping frequency.
51 /

4/Fosc

PRECAUTIONS

An internal RC oscillator and + 2 circuit provide timing signals to the level translator. The built-in regulator biases the
oscillator and divider to reduce power dissipation on high
supply voltage. The regulator becomes active at about V+
= 6.5V. Low voltage operation can be improved if the LV
pin is shorted to ground for V+ :;;; 3.5V. For V+ ;:;, 3.5V, the
LV pin must be left open to prevent damage to the part.

y+ (pin 8)

CrX ~

(pin 2) 52 /

C>---<1"j O-";"~""'-CTj 0 -

!L
Cp:_

Gnd (pin 3)

Wo'

J.
V

:

53 '

...n..nn.

54 ' .

~

"'~,

T-Cr

O-+-OVout = - y+
(pin 5)

TL/H/9136-6

FIGURE 2. Idealized Voltage Converter

3-133

ri:

o

~
en
o

used in ,...Power and battery back-up equipment. It must be
understood that the lower operating frequency and supply
current cause an increased impedance of Cr and Cpo The
increased impedance, due to a lower switching rate, can be
offset by raising Cr and Cp until ripple and load current requirements are met.

entire supply voltage and temperature range without the
need for an output diode. When replacing existing designs,
the LMC7660 can be operated with diode Dx.

Typical Applications
Changing Oscillator Frequency

Synchronizing to an External Clock

It is possible to dramatically reduce the quiescent operating
current of the LMC7660 by lowering the oscillator frequency. The oscillator frequency can be lowered from a nominal
10 kHz to several hundred hertz, by adding a slow-down
capacitor Cose (Rgure 3). As shown in the Typical Performance Curves the supply current can be lowered to the 10 p.A
range. This low current drain can be extremely useful when

Figure 4 shows an LMC7660 synchronized to an external
clock. The CMOS gate overrides the internal oscillator when
it is necessary to switch faster or reduce power supply interference. The external clock still passes through the + 2 circuit in the 7660, so the pumping frequency will be Yz the
external clock frequency.

TUH/9136-7

FIGURE 3. Reduce Supply Current by Lowering Oscillator Frequency

1k

TL/H/9136-6

FIGURE 4. Synchronizing to an External Clock

3-134

r-

Typical Applications

(Continued)

Lowering Output Impedance

current required for each stage is twice the load current on
that stage as shown in Figure 6A. The effective output resistance is approximately the sum of the individual Rout values, and so only a few levels of multiplication can be used.

Paralleling two or more LMC7660's lowers output impedance. Each device must have it's own pumping capacitor
Cpo but the reservoir capacitor Cr is shared as depicted in
Figure 5. The composite output resistance is:

Ei:
o.......
Q)
Q)

CI

It is possible to generate -15V from + 5V by connecting
the second 7660's pin 8 to + 5V instead of ground as
shown in Figure 68. Note that the second 7660 sees a full
20V and the input supply should not be increased beyond
+5V.

R
= Rout of one LMC7660
out
Number of devices
Increasing Output Voltage
Stacking the LMC7660s is an easy way to produce a greater
negative voltage. It should be noted that the input

8

2

7
LMC7660

6

7
LMC7660

6

5

TL/H/9136-9

FIGURE 5. Lowering Output Resistance by Paralleling Devices

7
LMC7660

TL/H/9136-10

FIGURE SA. Higher Voltage by Cascade

•
TL/H/9136-11

FIGURE SB. Getting -15Vfrom +5V

3-135

o

(/)
(/)

.....
o

:E
...I

Typical Applications

(Continued)

Split V+ In Half

Getting Up ••• and Down
The LMC7660 can also be used as a positive voltage multiplier. This application, shown in Figure 8, requires 2 additional diodes. During the first % cycle 82 charges Cp 1
through D1; D2 is reverse biased. In the next % cycle 82 is
open and S1 is closed. Since Cp 1 is charged to V+ - VOl
and is referenced to V+ through 81, the junction of D1 and
D2 is at V+ + (V+ -VOl)' D1 is reverse biased in this
interval. This application uses only two of the four switches
in the 7660. The other two switches can be put to use in
performing a negative conversion at the same time as
shown in Figure 9. In the % cycle that D1 is charging Cp1,
Cp2 is connected from ground to -Vout via 82 and 84, and
Cr2 is storing Cp2's charge. In the interval that 81 and S3
are closed, Cp1 pumps the junction of D1 and D2 above
V+, while Cp2 is refreshed from V+.

Figure 7 is one of the more interesting applications for the
LMC7660. The circuit can be used as a precision voltage
divider (for very light loads), alternately it is used to generate
a % supply point in battery applications. In the % cycle
when S1 and 83 are closed, the supply voltage divides
across the capacitors in a conventional way proportional to
their value. In the % cycle when 82 and 84 are closed, the
capacitors switch from a series connection to a parallel connection. This forces the capacitors to have the same voltage; the charge redistributes to maintain precisely V+ 12,
across Cp and Cr. In this application all devices are only
V+ 12, and the supply voltage can be raised to 20V giving
exactly 10V at Vout.

LMC7660

v+

'--------+....-Vout=z
C'l100J'F

TLiH/9l36-12

FIGURE 7. Split V+ in Half

TL/H/9136-l3

FIGURE 8. Positive Voltage Multiplier

3-136

Typical Applications

(Continued)

TL/H/9136-14

FIGURE 9. Combined Negative Converter and Positive Multiplier
the LMC7660 in a loop with a LP2951. The circuit of Figure
11 will regulate Vout to -5V for IL = 10 mA, and Yin = 6V.
For Yin > 7V, the output stays in regulation up to IL = 25
mA. The error flag on pin 5 of the LP2951 sets low when the
regulated output at pin 4 drops by about 5%. The LP2951
can be shutdown by taking pin 3 high; the LMC7660 can be
shutdown by shorting pin 7 and pin B.

Thermometer Spans 180"C
Using the combined negative and positive multiplier of Figure 10 with an LM35 it is possible to make a ,...Power thermometer that spans a 1BO·C temperature range. The LM35
temperature sensor has an output sensitivity of 10 mV
while drawing only 50 ,...A of quiescent current. In order for
the LM35 to measure negative temperatures, a pull down to
a negative voltage is required. Figure 10 shows a thermometer circuit for measuring temperatures from - 55·C to
+ 125·C and requiring only two 1.5V cells. End of battery life
can be extended by replacing the up converter diodes with
Schottky's.

rc,

The LP2951 can be reconfigured to an adjustable type regulator, which means the LMC7660 can give a regulated output from -2.0V to -10V dependent on the resistor ratios
R1 and R2, as shown in Figure 12, Vref = 1.235V:
Vout = Vref (1

Regulating -Vout

+ :~)

It is possible to regulate the output of the LMC7660 and still
maintain ,...Power performance. This is done by enclosing

8

47k

=

t-:-:::"'--"'OUTPUT 10 mV/OC

-55OC to + 1250C
'For lower voltage operation, use Schottky rectifiers

TL/H/st36-t5

fiGURE 10. ,...Power Thermometer Spans 180"C, and Pulls Only 150 ,...A

3-137

•

I

Typical Applications (Continued)
+Vin 6V

to

S.D. Input

25V

8

7
3

LP2951

......;t___

....._ _....IF-....- -....

4

6

330k
Error
....-'Output

5
.f~-

Regulated
-Vout

TLlH/9136-16

FIGURE 11, Regulated - 5V with 200 /LA Standby Current

+V1n 6V

to

S.O. Input

3
4

LP295 I

6
5

25V

330k
Error

....._ _.....F-.....- .....- ....~....._ _.....F-+-....-Output
R2

VOu!

= Vref ( 1 + ~D

Rl

V,ef = 1.235V
TL/H/9136-17

'Low voltage operation

FIGURE 12. LMC7660 and LP2951 Make a Negative Adjustable Regulator

3·138

Section 4
Motion Control

Section 4 Contents
Motion Control and Motor Drive Selection Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM 12L 80W Operational Amplifier . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . • .
LM621 Brushless Motor Commutator ..........•.........•..•..•..............•.......
LM628/LM629 Precision Motion Controllers ...........................................
LM18293 Four Channel Push-Pull Driver. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM18298 Dual Full-Bridge Driver. . . . . . . . . . . . . • . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LMD18200 3A, 55VH-Bridge . . . . . . . • . . . . . . . . . . . . • . . . . . • . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LMD18201 3A, 55VH-Bridge ... ... ... .... ....... ... .. ... .. ..... .•. .•.... .... .........

4-2

4-3
4-4
4-17
4-28
4-49
4-55
4-61
4-70

s::
o

-

~Nationai

O·
o
o
::I

::I

Semiconductor

2-

Motion Control and Motor Drive Selection Guide

I»
::I

Q.

s::
o
..,8"

Motor Drive Circuits-Bridges

..,c

Device

Description

Output
Current
(A)

LMD18200

DMOS H·Bridge with Internal Current Sense

3

LMD18201

DMOS H-Bridge

LM18293

4-Channel Push-Pull Driver

LM18298

Dual H-Bridge

Max Input
Voltage
(V)

Operating
Temperature
(TJ)

Package
Availability

Page
No.

55

- 40'C to + 125'C

11-Lead TO-220

4-61

~.

en
CD

CD
~

O·

3

55

-40'C to + 125'C

11-Lead TO-220

4-70

::I

1/Channel

36

-40'C to + 125'C

16-Lead DIP

4-49

G)

2/Bridge

46

-40'C to + 150'C

15-Lead TO-220

4-55

a:
CD

C

Motor Drive Circuits-Linear
Device

LM12

Description

Output
Current
(A)

Max Supply
Voltage
(V)

Operating
Temperature
(Te)

Package
Availability

Page
No.

Monolithic Power Op-Amp

±10

±30

- 55'C to + 125'C

4-LeadTO-3

4-4

Brushless DC Motor Commutator
Device

Operating
Temperature

Features

(TA)
LM621

Compatible with 3-Phase and 4-Phase Brushless DC Motors, Interfaces
Directly to Hall Sensors and PWM Sign and Magnitude Signals, Adjustable
Dead Time Generator

-40'Cto +85'C

Package
Availability

Page
No.

18-Lead DIP

4-17

Precision Motion Control Processor
Device

Features

Operating
Temperature
(TA)

Max Clock
Speed
(MHz)

Package
Availability

Page
No.

LM628

32-Bit Position, Velocity, and Acceleration Registers; Position and
Velocity Modes; 16-Bit PI D Filter with Programmable Coefficients;
8- or 12-Bit DAC Output Data; Quadrature Incremental
Encoder Interface; 8-Bit Asynchronous Host Interface

-40'Cto +85'C

60r8

28-LeadDIP

4-28

Same Features as LM628, but with 8-Bit
PWM Sign/Magnitude Output Data

-40'Cto +85'C

60r8

28-Lead DIP

4-28

LM629

4-3

•

CN
,..

::E
...I

,----------------------------------------------------------------------------,

~National

~ Semiconductor

lM 12 (l) BOW Operational Amplifier
General Description
The LM12 is a power op amp capable of driving ±25Vat
±10A while operating from ±30V supplies. The monolithic
IC can deliver SOW of sine wave power into a 40 load with
0.01 % distortion. Power bandwidth is 60 kHz. Further, a
peak dissipation capability of SOOW allows it to handle reactive loads such as transducers, actuators or small motors
without derating. Important features include:
• input protection
• controlled turn on
• thermal limiting
• overvoltage shutdown
• output-current limiting
• dynamic safe-area protection
The IC delivers ± 1OA output current at any output voltage
yet is completely protected against overloads, including
shorts to the supplies. The dynamic safe-area protection is
provided by instantaneous peak-temperature limiting within
the power transistor array.

exceeds 150'C or as the supply voltage approaches the
BYCEO of the output transistors. The IC withstands overvoltages to SOY.
This monolithic op amp is compensated for unity-gain feedback, with a small-signal bandwidth of 700 kHz. Slew rate is
9V IlLs, even as a follower. Distortion and capacitive-load
stability rival that of the best designs using complementary
output transistors. Further, the IC withstands large differential input voltages and is well behaved should the commonmode range be exceeded.
The LM12 establishes that monolithic ICs can deliver considerable output power without resorting to complex switching schemes. Devices can be paralleled or bridged for even
greater output capability. Applications include operational
power supplies, high-voltage regulators, high-quality audio
amplifiers, tape-head positioners, x-y plotters or other servo-control systems.
The LM12 is supplied in a four-lead, TO-3 package with yon the case. A gold-eutectic die-attach to a molybdenum
interface is used to avoid thermal fatigue problems. The
LM12 is specified for either military or commercial temperature range.

The turn-on characteristics are controlled by keeping the
output open-circuited until the total supply voltage reaches
14Y. The output is also opened as the case temperature

Typical Application *

Connection Diagram
4·pln glass epoxy TO·3
socket is available from
AUGATINC.

r--+-"IM---4- AA,n '------ OUT

OUT
1.1k

IN~+----1

lk
common
ground",
point
";

+IN

v-v+
TL/H/B704-2

nCASE)
'Low distortion (0.01 %) audio amplifier

TL/H/B704-1

Bottom View
Order Number LM12LK or LM12CLK
See NS Package Number K04A

4-4

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Total Supply Voltage (Note 1)
80V
Input Voltage
Output Current

(Note 3)

Junction Temperature
Storage Temperature Range

- 65'C to 150'C

Lead Temperature (Soldering, 10 seconds)

300'C

Operating Ratings

(Note 2)
Internally Limited

15Vto 60V

Total Supply Voltage

Electrical Characteristics (Note 4)
Parameter

Conditions

Typ
25'C

LM12L

LM12CL

Limits

Limits

2

7/15

15/20

mV(max)

Units

Input Offset Voltage

±10V:S;Vs:S; ±0.5VMAX,
VCM = 0

Input Bias Current

V- + 4V:s; VCM :s; V+ -2V

0.15

0.3/1.0

0.7/1.0

p.A(max)

Input Offset Current

V

+4V:s; VCM:S; V+ -2V

0.03

0.1/0.3

0.2/0.3

p.A(max)

Common Mode
Rejection

V

+4V:S; VCM :s; V+ -2V

86

75/70

70/65

dB (min)

Power Supply
Rejection

V+ = 0.5 VMAX,
-6V <: V- <: -0.5 VMAX
V- = -0.5 VMAX,
6V:S; V+ :s; 0.5 VMAX

90

75170

70/65

110

80175

75/70

dB (min)

tON = 1 ms,
~VIN = 5 (10) mY,
lOUT = 1A
8A
10A

1.8
4
5

2.2/2.5

2.2/2.5
5/7

V (max)
V (max)
V (max)

tON = 2ms,
VSAT = 2V, lOUT = 0
VSAT = 8V, RL = 41"1.

100
50

20/15

30/20
15/10

V/mV(min)
V/mV(min)

30

50

100

p.V/W(max)

Output Saturation
Threshold

Large Signal Voltage
Gain

517
8
50/30

dB (min)

Thermal Gradient
Feedback

POISS = 50W, toN = 65 ms

Output-Current
Limit

toN = 10 ms, VOISS = 10V

13

16

16

A (max)

toN = 100 ms, VOISS = 58V

1.5
1.5

1.0/0.6

0.9/0.6

1.7

1.7

A (min)
A (max)
W(min)
W(min)

Power Dissipation
Rating

toN = 100 ms, VOISS = 20V
VOISS = 58V

100
80

90/40

80/55

58/35

52/35

DC Thermal Resistance

(Note 5)

2.3
2.7

2.6
4.0

2.9
4.5

'C/W(max)
'C/W(max)
'C/W(max)

VOISS = 20V
VOISS = 58V

AC Thermal Resistance

(Note 5)

1.6

1.9

2.1

Supply Current

VOUT = 0, lOUT = 0

60

80/90

120/140

mA(max)

Note 1: These are non-operating limits (over.voltage shut down); operating limits are as in Note 4. With inductive loads or output shorts. other restrictions described
In applications section apply.
Note 2. Neither Input should exceed the supply voltage by more than SO volts nor should the voltage between one input and any other tenninal exceed 60 volts.
Note 3. Operating iunction temperature is internally limited near 225'C within the power transistor and 16O'C for the control circuitry.
Note 4. The supply voltage is ±30V (VMAX = 60V). unless otherwise specified. The voltage across the conducting output transistor (supply to output) is VOISS and
internal power dissipation is POISS. Temperature range is -SS'C ,;: TC ,;: 12S'C for the LM12L and O'C ,;: Tc ,;: 70'C for LM12CL. where Tc Is the case
temperature. Standard typeface Indicates limits at 2S'C while boldface type refers to limits or special conditions over full temperature range. With no heat
sink, the package will heat at a rate of 3S'C/sec per 100W of internal dissipation.
Nota 5. This thermal resistance is based upon a peak temperature of 200'C in the center of the power transistor and a case temperature of 25'C measured at the
center of the package bottom. The meximum junction temperature of the control circuitry can be estimated based upon a dc thermal resistance of O.f1'C/W or an BC
thennal resistance of O.6'C/W for any operating voltage.
Although the output and supply leads are resistant to electrostatic discharges from handling, the input leads are not.
The part should be treated accordingly.

4-5

N

:s..-

Output-Transistor Ratings (guaranteed)t
Safe Area
10
'00=0.3 ...

3

I6

I

'" ........ ......

5.0

"- ......
'I'.. I'-...

Pulse Thermal Resistance

TJ =20Doe
TC=2S0C70 D C---

VCE=.OV- Tc=2SoC I
S8V---TJ =200 o C

_12Soc-

I-

1.0

I"t--...: ~ ~

2.0

........

Tc=2SoC
TJ =200 o C

1.0

0.5

DC Thermal Resistance

~

2

o

20

.0

...

./

~~

60

o

COLLECTOR-EMITTER VOLTAGE (V)

~

....

~

;.... !-'

-

Io

20

~

0.1

60

.0

1.0

GOLLECTOR-ENITTER VOLTAGE (V)

100

10

PULSE WIDTH (ms)

TL/H/8704-3
tLMI2L. The power ratings of the LM12CL are 10'percerrtless at20V and 15-percentless at 60V. with a corresponding Increase In 1hermal resisfance and

decrease in safe area current.

.

Typical Performance Characteristics
Pulse Power Limit

Pulse Power Limit

500

120

Peak Output Current
16

Tc=~50C

1080

~

60

Tc= tl25 0 C

100

12

Vs =:t30V

III

40

toN = lOOms
20 I-D

o
o

100

10

TIME (m.)

r... ;;:::
.-

-

J.

IoUT=il~

-50

~

g

=:l:30V

~

,

THD"S%
I\. =411

1\

10

CASE TENPERTATURE (0 C)

10

iil
s
:=
5

r

-ID

I
II

\
\
\1"

-20

o
150

1.6

Follower Pulse Response

E
Vs

iil

100

1.2

0.8

30

20

~

C:= ..-

u

V1N =:l:15V

~

1
50

Large Signal Response

.;!!,

iSA

=100°C'"

=2S o C
1.1

Tc

TINE (ml)

30

S

i8A

o

60

20

I)

ilA

40

20

o
o

GOLLECTOR-ENITTER VOLTAGE (V)

Output Saturation Voltage
toN = 1 m.
I II

I

'" -----Tc

TUN = 230 C

1.0

Your = 0

r;:: r-

-

-30
lOOk

10k

FREQUENCY (Hz)

1M

D

10

15

20

25

30

TIWE (}Os)

TUH/B704-4

4·6

Typical Performance Characteristics
Large Signal Gain

(Continued)

Thermal Response

50

'>E

~

~

I
S~URC~ _

40

- -1'- -

30

~

20

~

10

1,'

Vs=UOV
YOUT II :t25Y

~

-I

-50

50

100

ISO

I

o

"

I

20

40

",

••

40

180
,GAIN

'-PHASE',,-

90

45

"\:
r'\
100

1
~

"'\

10

I
"

~

~

I

-45

~ -0

-I

1.0

FREQUENCY (Hz)

\

:>

0.2

VCM = -25V

o

~~

:'o..VCM =25V

~

u

...;;: ~
1"""=

-50

50

100

Ik

120

I
I

Tell 1250 C

I

o

o

I

-

10

20

SUPPLY VOLTAGE (iV)

30

v.vs

20
-40

f I

-20

u

20

'L =0
0.2

•

0.1

II I

OUTPUT VOLTAGE (V)

0.3

ffi

II!
:>

=:t:30V

f- ,...Vs=UOV

•

""_JUJ

Vour=USV

3

~

40

I J

0.4

I
I

~

C

1M

Cross-Supply Current

lOUT = 0

......

lOOk

0.5

Tc=2Soc

100

1Tc=!;:7
Tc

10k

FREQUENCY (Hz)

I I

".=-55 O

'f"""

20 ' Ik

lOOk

Supply Current

I
I

~

V-

10k

"-

f-

FREQUENCY (Hz)

Supply Current
f-VOUT=O
80 '"""lour=O

100

'"""

i'

'"""

10
10

1M

-

r-

80 f-

40

ISO

100

lOOk

Common Mode Rejection

~

§

10k

FREQUENCY (Hz)

~
'"""
80 f-

CASE TEMPERATURE (0 C)

100

Ik

100

~
z

I I

20

0
100

10M

~.!

~

0.4

1A

40

Input Noise Voltage

Vs=UOV

i

l!l

§
iil

1M

80

~

Ik

0.8

.3

....

FREQUENCY (Hz)

Input Bias Current

-:c

10k

Power Supply Rejection

,

~,

.
0.1
lOOk

0.8

Ik

80

g

10k lOOk I M 10M

Ik

100

FREQUENCY (Hz)

10

135 Ii'

-20

80

Output Impedance
225

20

80

TIME (ml)

Frequency Response

........
,

~

is

CASE TEMPERATURE (Oc)

80

z

~

SINK

~PON=50W

f= 100Hz

100

g

/.

1\ = 4R

o

80

Total Harmonic Distortion
0.1

40

..
o Ik

3k

1\ =4R

10k

30k

lOOk

FREQUENCY (Hz)

TL/H/8704-5

4-7

~

.....

:i

r------------------------------------------------------------------------------------------,
Application Information
The current in the supply leads is a rectified component of
the load current. If adequate bypassing is not provided, this
distorted signal can be fed back into internal circuitry. Low
distortion at high frequencies requires that the supplies be
bypassed with 470 p.F or more, at the package terminals.

GENERAL
Twenty five years ago the operational amplifier was a specialized design tool used primarily for analog computation.
However, the availability of low cost IC op amps in the late
1960's prompted their use in rather mundane applications,
replacing a few discrete components. Once a few basic
principles are mastered, op amps can be used to give exceptionally good results in a wide range of applications
while minimizing both cost and design effort.

LEAD INDUCTANCE
With ordinary op amps, lead-inductance problems are usually restricted to supply bypassing. Power op amps are also
sensitive to inductance in the output lead, particularly with
heavy capacitive loading. Feedback to the input should be
taken directly from the output terminal, minimizing common
inductance with the load. Sensing to a remote load must be
accompanied by a high-frequency feedback path directly
from the output terminal. Lead inductance can also cause
voltage surges on the supplies. With long leads to the power
source, energy stored in the lead inductance when the output is shorted can be dumped back into the supply bypass
capaCitors when the short is removed. The magnitude of
this transient is reduced by increasing the size of the bypass
capacitor near the IC. With 20 p.F local bypass, these voltage surges are important only if the lead length exceeds a
couple feet (> 1 p.H lead inductance). Twisting together the
supply and ground leads minimizes the effect.

The availability of a monolithic power op amp now promises
to extend these advantages to high-power designs. Some
conventional applications are given here to illustrate op amp
design principles as they relate to power circuitry. The inevitable fall in prices, as the economies of volume production
are realized, will prompt their use in applications that might
now seem trivial. Replacing single power transistors with an
op amp will become economical because of improved performance, simplification of attendant circuitry, vastly improved fault protection, greater reliability and the reduction
of design time.
Power op amps introduce new factors into the design equation. With current transients above lOA, both the inductance
and resistance of wire interconnects become important in a
number of ways. Further, power ratings are a crucial factor
in determining performance. But the power capability of the
IC cannot be realized unless it is properly mounted to an
adequate heat sink. Thus, thermal design is of major importance with power op amps.

GROUND LOOPS
With fast, high-current cirCUitry, all sorts of problems can
arise from improper grounding. In general, difficulties can be
avoided by returning all grounds separately to a common
point. Sometimes this is impractical. When compromising,
special attention should be paid to the ground returns for
the supply bypasses, load and input signal. Ground planes
also help to provide proper grounding.

This application summary starts off by identifying the origin
of strange problems observed while using the LM12 in a
wide variety of designs with all sorts of fault conditions. A
few simple precautions will eliminate these problems. One
would do well to read the section on supply bypassing,
lead inductance, output clamp diodes, ground loops
and reactive loading before doing any experimentation.
Should there be problems with erratic operation, blowouts, excessive distortion or oscillation, another look at
these sections is In order.

Many problems unrelated to system performance can be
traced to the grounding of line-operated test equipment
used for system checkout. Hidden paths are particularly difficult to sort out when several pieces of test equipment are
used but can be minimized by using current probes or the
new isolated oscilloscope pre-amplifiers. Eliminating any direct ground connection between the Signal generator and
the oscilloscope synchronization input solves one common
problem.

The management and protection circuitry can also affect
operation. Should the total supply voltage exceed ratings or
drop below IS-20V, the op amp shuts off completely. Case
temperatures above ISO"C also cause shut down until the
temperature drops to 14SoC. This may take several seconds, depending on the thermal system. Activation of the
dynamic safe-area protection causes both the main feedback loop to lose control and a reduction in output power,
with possible oscillations. In ac applications, the dynamic
protection will cause waveform distortion. Since the LM12 is
well protected against thermal overloads, the suggestions
for determining power dissipation and heat sink requirements are presented last.

OUTPUT CLAMP DIODES
When a push-pull amplifier goes into power limit while driving an inductive load, the stored energy in the load inductance can drive the output outside the supplies. Although
the LM12 has internal clamp diodes that can handle several
amperes for a few milliseconds, extreme conditions can
cause destruction of the IC. The internal clamp diodes are
imperfect in that about half the clamp current flows into the
supply to which the output is clamped while the other half
flows across the supplies. Therefore, the use of external
diodes to clamp the output to the power supplies is strongly
recommended. This is particularly important with higher supply voltages.

SUPPLY BYPASSING
All op amps should have their supply leads bypassed with
low-inductance capacitors having short leads and located
close to the package terminals to avoid spurious oscillation
problems. Power op amps require larger bypass capacitors.
The LM12 is stable with good-quality electrolytiC bypass capacitors greater than 20 p.F. Other considerations may require larger capacitors.

Experience has demonstrated that hard-wire shorting the
output to the supplies can induce random failures if these
external clamp diodes are not used and the supply voltages
are above ± 20V. Therefore it is prudent to use output-

4-8

r-

3:
....
N

Application Information

(Continued)
clamp diodes even when the load is not particularly inductive. This also applies to experimental setups in that blowouts have been observed when diodes were not used. In
packaged equipment, it may be possible to eliminate these
diodes, providing that fault conditions can be controlled.

and expected nature of the load, but are not critical. A 4 p.H
inductor is obtained with 14 turns of number 1a wire, close
spaced, around a one-inch-diameter form.

Dl

OUT

IN

> -..........-OUT
IN

--------+-v-

D2

TL/H/B704-B

The LM12 can be made stable for all loads with a large
capaCitor on the output, as shown above. This compensation gives the lowest possible closed-loop output impedance at high frequencies and the best load-transient response. It is appropriate for such applications as voltage
regulators.
A feedback capaCitor, Cl, is connected directly to the output
pin of the IC. The output capacitor, C2, is connected at the
output terminal with short leads. Single-point grounding to
avoid dc and ac ground loops is advised.

TL/H/B704-6

Heat sinking of the clamp diodes is usually unimportant in
that they only clamp current transients. Forward drop with
15A fault transients is of greater concern. Usually, these
transients die out rapidly. The clamp to the negative supply
can have somewhat reduced effectiveness under worst
case conditions should the forward drop exceed 1.0V.
Mounting this diode to the power op amp heat sink improves
the situation. Although the need has only been demonstrated with some motor loads, including a third diode (D3
above) will eliminate any concern about the clamp diodes.
This diode, however, must be capable of dissipating continuous power as determined by the negative supply current of
the op amp.

The impedance, ZI, is the wire connecting the op amp output to the load capacitor. About 3-inches of number-I a wire
(70 nH) gives good stability and la-inches (400 nH) begins
to degrade load-transient response. The minimum load capaCitance is 47 p.F, if a solid-tantalum capaCitor with an
equivalent series resistance (ESR) of 0.10 is used. Electrolytic capaCitors work as well, although capaCitance may
have to be increased to 200 p.F to bring ESR below 0.10.
Loop stability is not the only concern when op amps are
operated with reactive loads. With time-varying signals,
power dissipation can also increase markedly. This is particularly true with the combination of capacitive loads and
high-frequency excitation.

REACTIVE LOADING
The LM12 is normally stable with resistive, inductive or
smaller capacitive loads. Larger capacitive loads interact
with the open-loop output resistance (about 10) to reduce
the phase margin of the feedback loop, ultimately causing
oscillation. The critical capacitance depends upon the feedback applied around the amplifier; a unity-gain follower can
handle about 0.Q1 p.F, while more than 1 p.F does not cause
problems if the loop gain is ten. With loop gains greater than
unity, a speedup capacitor across the feedback resistor will
aid stability. In all cases, the op amp will behave predictably
only if the supplies are properly bypassed, ground loops are
controlled and high-frequency feedback is derived directly
from the output terminal, as recommended earlier.
So-called capacitive loads are not always capacitive. A
high-Q capaCitor in combination with long leads can present
a series-resonant load to the op amp. In practice, this is not
usually a problem; but the situation should be kept in mind.

INPUT COMPENSATION
The LM12 is prone to low-amplitude oscillation bursts coming out of saturation if the high-frequency loop gain is near
unity. The voltage follower connection is most susceptible.
This glitching can be eliminated at the expense of smail-signal bandwidth using input compensation. Input compensation can also be used in combination with LR load isolation
to improve capacitive load stability.

L1
4p.
OUT
IN~--'\iy.,+--1

>-+...J.>N\,..........IN

OUT

Rl
4.7
TLiH/B704-7

TLiH/B704-9

Large capacitive loads (including series-resonant) can be
accommodated by isolating the feedback amplifier from the
load as shown above. The inductor gives low output impedance at lower frequencies while providing an isolating impedance at high frequencies. The resistor kills the Q of series resonant circuits formed by capacitive loads. A low inductance, carbon-composition resistor is recommended.
Optimum values of Land R depend upon the feedback gain

An example of a voltage follower with input compensation is
shown here. The R2C2 combination across the input works
with Rl to reduce feedback at high frequencies without
greatly affecting response below 100 kHz. A lead capacitor,
Cl, improves phase margin at the unity-gain crossover frequency. Proper operation requires that the output impedance of the Circuitry driving the follower be well under I kO
at frequencies up to a few hundred kilohertz.
4-9

CN
..-

:i

.-------------------------------------------------------------------------------~

Application Information

(Continued)
equalization resistors. More output buffers, with individual
equalization resistors, may be added to meet even higher
drive requirements.

IN.y,~P--""'---1

R3

5k
C2

OUT

0.22~ t - -.....""

><....W_~'""OUT
IN

Rl

lk

TL/H/8704-10

Extending Input compensation to the integrator connection
Is shown here. Both the follower and this Integrator will handle 1 /JoF capacitive loading without LA output Isolation.

TL/H/8704-13

CURRENT DRIVE

R2'

Rl'
10k

10k

lOUT

This connection allows Increased output capability without
requiring a separate control amplifier. The output buffer, A2,
provides load current through A5 equal to that supplied by
the main amplifier, Al, through R4' Again, more output buffers can be added.
Current sharing among paralleled amplifiers can be affected
by gain error as the power-bandwidth limit Is approached. In
the first circuit, the operating current increase will depend
upon the matching of high-frequency characteristics. In the
second circuit, however, the entire Input error of A2 appears
across R4 and R5. The supply current Increase can cause
power limiting to be activated as the slew limit Is approached. This will not damage the LM 12. It can be avoided
In both cases by connecting A1 as an Inverting amplifier and
restricting bandwidth with C1.

R2VIN

= fii""Re'

>-....WIr-4'""OUT

• PRECISION RESISTORS
TL/H/8704-11

This circuit provides an output current proportional to the
Input voltage. Current drive Is sometimes preferred for servo
motors because It aids in stabilizing the servo loop by reducIng phase lag caused by motor Inductance. In applications
requiring high output resistance, such as operational power
supplies running in the current mode, matching of the feedback resistors to 0,01 % Is required. Alternately, an adJustable resistor can be used for trimming.

SINGLE-SUPPLY OPERATION

PARALLEL OPERATION

+IN -'IIvv--....- -......W ...."'"

R4
0.1

IN

> ...WII-4,""'OUT
R5
0.1

-IN ...I\I----.Jt.JV\r

TLlH/6704-15

TL/H/6704-16

The voltage swing delivered to the load can be doubled by
using the bridge connection shown here. Output clamping to
the supplies can be provided by using a bridge-rectifier assembly.

200p

R2
10k

One limitation of the standard bridge connection is that the
load cannot be returned to ground. This can be circumvented by operating the bridge with floating supplies, as shown
above. For single-ended drive, either input can be grounded.

R3

C2

470 0.22J'

=30V

IN"'V\,..,..t--.I\{\;~-t-...I\{'."""'-U-""--+-~""...,

R1
1k

R6
Sk

>-........ OUT

TL/H/6704-17

This circuit shows how two amplifiers can be cascaded to double output swing. The advantage over the bridge is that the output
can be increased with any number of stages, although separate supplies are required for each.

OUT
R13
3.3

R1
1k
0.1%

TL/H/6704-16

Discrete transistors can be used to increase output drive to ± 70V at ± 10A as shown above. With proper thermal design, the IC
will provide safe-area protection for the external transistors. Voltage gain is about thirty.

4-11

....
:i

~ ~--------------------------------------------------------------------------------,

Application Information

(Continued)

OPERATIONAL POWER SUPPLY

Note: Supply voltages for the
LM318s are ± 15V

-15V

R9
2.05k
1%

R6
12k
1%

R7
12k
1%
OUT

R12
lk

-

IN

C5
75p
TUH/8704-19

External current limit can be provided for a power op amp as shown above. The positive and negative current limits can be set
precisely and independently. Fast response is assured by Dl and D2. Adjustment range can be set down to zero with potentiometers Ra and R7. Alternately, the limit can be programmed from a voltage supplied to R2 and Rs. This is the set up required for
an operational power supply or voltage-programmable power source.

SERVO AMPLIFIERS
When making servo systems with a power op amp, there is
a temptation to use it for frequency shaping to stabilize the
servo loop. Sometimes this works; other times there are
better ways; and occasionally it just doesn't fly. Usually it's a
matter of how quickly and to what accuracy the servo must
.
stabilize.
R5
10k
0.1%

Rl
10k

INJ\I'.fv-+-WHI-.....--¥./'v--..,
R4
lk

TUH/8704-21

This position servo uses an op amp to develop the rate
signal electrically instead of using a tachometer. In high-performance servos, rate signals must be developed with large
error signals well beyond saturation of the motor drive. Using a separate op amp with a feedback clamp allows the
rate signal to be developed properly with pOSition errors
more than an order of magnitude beyond the loop-saturation level as long as the photodiode sensors are pOSitioned
with this in mind.

TL/H/8704-20

This motor/tachometer servo gives an output speed proportional to input voltage. A low-level op amp is used for frequency shaping while the power op amp provides current
drive to the motor. Current drive eliminates loop phase shift
due to motor inductance and makes high-performance servos easier to stabilize.

4-12

r-

Application Information

5:
.....
N

(Continued)

VOLTAGE REGULATORS
R1
1.7k

REMOTE SENSING

y+~ 55V

R3
SOk

-IN

>-_"-'+'-OUT

C2
1n

~

D1

LM385
2.5V

'--+-----+-GND
R3
700

TL/H/B704-24

TL/H/B704-22

Remote sensing as shown above allows the op amp to correct for dc drops in cables connecting the load. Even so,
cable drop will affect transient response. Degradation can
be minimized by using twisted, heavy-gauge wires on the
output line. Normally, common and one input are connected
together at the sending end.

An op amp can be used as a positive or negative regulator.
Unlike most regulators, it can sink current to absorb energy
dumped back into the output. This positive regulator has a
0-50V output range.

R1

AUDIO AMPLIFIERS

36k

R2
1.1k

> .....-t---+OUT

IN

R1
1k

R2
2.7k

common

ground /
point ':'

D1
LW329

7V

R3
4k

TLlH/B704-25

A power amplifier suitable for use in high-quality audio
equipment is shown above. Harmonic distortion is about
Om-percent. Intermodulation distortion (60 Hz/? kHz, 4:1)
measured 0.015-percent. Transient response and saturation
recovery are clean, and the 9 V / ,,"S slew rate of the LM12
virtually eliminates transient intermodulation distortion. Using separate amplifiers to drive low- and high-frequency
speakers gets rid of high-level crossover networks and attenuators. Further, it prevents clipping on the low-frequency
channel from distorting the high frequencies.

L---4--4-+---.....+---4~~-+--~~GND
TL/H/B704-23

Dual supplies are not required to use an op amp as a voltage regulator if zero output is not required. This 4V to 50V
regulator operates from a single supply. Should the op amp
not be able to absorb enough energy to control an overvoltage condition, a SCR will crowbar the output.

•
4-13

....

~ ~----------------------------------------------------------------------------.

!i

Application Information

(Continued)

DETERMINING MAXIMUM DISSIPATION

audio applications. The peak dissipation of each transistor is
about four times average. In ac applications, power capability is often limited by the peak ratings of the power transistor.

It is a simple matter to establish power requirements for an
op amp driving a resistive load at frequencies well below
10 Hz. Maximum dissipation occurs when the output is at
one-half the supply voltage with high-line conditions. The
individual output transistors must be rated to handle this
power continuously at the maximum expected case temperature. The power rating is limited by the maximum junction
temperature as determined by

The pulse thermal resistance of the LM 12 is specified for
constant power pulse duration. Establishing an exact equivalency between constant-power pulses and those encountered in practice is not easy. However, for sine waves, reasonable estimates can be made at any frequency by assuming a constant power pulse amplitude given by:

TJ = Tc + POISS 8JC,
where T c is the case temperature as measured at the center of the package bottom, POISS is the maximum power
dissipation and 8JC is the thermal resistance at the operating voltage of the output transistor. Recommended maximum junction temperatures are 200"C within the power transistor and 150'C for the control circuitry.
If there is ripple on the supply bus, it is valid to use the
average value in worst-case calculations as long as the
peak rating of the power transistor is not exceeded at the
ripple peak. With 120 Hz ripple, this is 1.5 times the continuous power rating.
Dissipation requirements are not so easily established with
time varying output Signals, especially with reactive loads.
Both peak and continuous dissipation ratings must be taken
into account, and these depend on the signal waveform as
well as load characteristics.

PPK ..

DISSIPATION DRIVING MOTORS
A motor with a locked rotor looks like an inductance in series with a resistance, for purposes of determining driver
dissipation. With slow-response servos, the maximum signal
amplitude at frequencies where motor inductance is significant can be so small that motor inductance does not have
to be taken into account. If this is the case, the motor can
be treated as a simple, resistive load as long as the rotor
speed is low enough that the back emf is small by comparison to the supply voltage of the driver transistor.

With a sine wave output, analysis is fairly straightforward.
With supply voltages of ± Vs, the maximum average power
dissipation of both output transistors is
=
2VS2
P
MAX
'/T2 ZLcos8'

8

A permanent-magnet motor can build up a back emf that is
equal to the output swing of the op amp driving it. Reversing
this motor from full speed requires the output drive transistor to operate, initially, along a load line based upon the motor resistance and total supply voltage. Worst case, this
load line will have to be within the continuous dissipation
rating of the drive transistor; but system dynamics may permit taking advantage of the higher pulse ratings. Motor inductance can cause added stress if system response is
fast.
Shunt- and series-wound motors can generate back emf's
that are considerably more than the total supply voltage,
resulting in even higher peak dissipation than a permanentmagnet motor having the same locked-rotor resistance.

< 40';

and
PMAX =

~~: [;: -

COS8],

8

~ 40',

where ZL is the magnitude of the load impedance and 8 its
phase angle. Maximum average diSSipation occurs below
maximum output swing for 8 < 40'.
100 r--'---:-:~~!:'::":'-.--'---'
Vour= t25V

9=400

80

g
z

60

~
g,

40

II-

Vour =:t19.1V
9=0_

III

I

20

J

/ ., V

~

I

)r
0

30

I ~

VOLTAGE REGULATOR DISSIPATION
The pass transistor dissipation of a voltage regulator is easily determined in the operating mode. Maximum continuous
dissipation occurs with high line voltage and maximum load
current. As discussed earlier, ripple voltage can be averaged if peak ratings are not exceeded; however, a higher
average voltage will be required to insure that the pass transistor does not saturate at the ripple minimum.
Conditions during start-up can be more complex. If the input
voltage increases slowly such that the regulator does not go
into current limit charging output capacitance, there are no
problems. If not, load capacitance and load characteristics
must be taken into account. This is also the case if automatic restart is required in recovering from overloads.

I/ :\

0

-'"~\
\

Vs=:t30V
ZL =4A/COS 9

60

90

120

150

~~: [ 1-cos (",-8) ],

where ", = 60' and 8 is the absolute value of the phase
angle of ZL. Equivalent pulse width is toN .. 0.47 for 8 = 0
and toN "" 0.27 for 8 ~ 20', where 7 is the period of the
output waveform.

180

CONDUCTION ANGLE (DEGREES)
TL/H/8704-26

The instantaneous power dissipation over the conducting
half cycle of one output transistor is shown here. Power
dissipation is near zero on the other half cycle. The output
level is that resulting in maximum peak and average dissipation. Plots are given for a resistive and a series RL load. The
latter is representative of a 40 loudspeaker operating below
resonance and would be the worst case condition in most

Automatic restart or start-up with fast-rising input voltages
cannot be guaranteed unless the continuous dissipation rating of the pass transistor is adequate to supply the load
current continuously at all voltages below the regulated output voltage. In this regard, the LM 12 performs much better
than IC regulators using foldback current limit, especially
with high-line input voltage above 20V.
4-14

,-----------------------------------------------------------------------------,
Application Information

(Continued)

N

POWER LIMITING
40

Vs

30

.E
~

20

V

V

10

J/
-20 V

!; -10

l!:

6

r\

case temperature is almost entirely dependent on heat sink
design and the mounting of the IC to the heat sink.

=.t.40V

TC ~ 30~C

1 r ........

100
.~

I \ CURRENT

~

...!!l
'"...

VOLTAGE

\ /
......

I""'

-40
10

15

20

TI~E

(m.l

25

30

50 ~

r-....

'":::>
!;;:

-6

...'"
a....

-8

5

'" i'o....
"- I'. ......

'U'

\

-30

~

...==

0-

35
TL/H/8704-27

Should the power ratings of the LM12 be exceeded, dynamic safe-area protection Is activated. Waveforms with this
power limiting are shown for the LM12 driving ±26V at
30 Hz into 30 in series with 24 mH (8 = 45'). With an
inductive load, the output clamps to the supplies in power
limit, as above. With resistive loads, the output voltage
drops in limit. Behavior with more complex RCL loads is
between these extremes.
Secondary thermal limit is activated should the case temperature exceed 150'C. This thermal limit shuts down the IC
completely (open output) until the case temperature drops
to about 145'C. Recovery may take several seconds.

........
20

10
200

P=80W

50

r-.

~ i'r-.
......

i'r-.

500

"~

1000

HEAT-SINK AREA

On 2)

2000
TL/H/8704-28

The design of heat sink is beyond the scope of this work.
Convectlon·cooled heat sinks are available commercially,
and their manufacturers should be consulted for ratings.
The preceding figure is a rough guide for temperature rise
as a function of fin area (both sides) available for convection
cooling.
Proper mounting of the IC is required to minimize the thermal drop between the package and the heat sink. The heat
sink must also have enough metal under the package to
conduct heat from the center of the package bottom to the
fins without excessive temperature drop.
A thermal grease such as Wakefield type 120 or Thermalloy
Thermacote should be used when mounting the package to
the heat sink. Without this compound, thermal resistance
will be no better than 0.5'C/W, and probably much worse.
With the compound, thermal resistance will be O.2'C/W or
less, assuming under 0.005 inch combined flatness runout
for the package and heat sink. Proper torquing of the
mounting bolts Is important. Four to six inch-pounds is recommended.
Should it be necessary to isolate V- from the heat sink, an
insulating washer is required. Hard washers like berylium
oxide, anodized aluminum and mica require the use of thermal compound on both faces. Two-mil mica washers are
most common, giving about 0.4'C/W interface resistance
with the compound. Silicone-rubber washers are also available. A 0.5'C/W thermal resistance is claimed without thermal compound. Experience has shown that these rubber
washers deteriorate and must be replaced should the IC be
dismounted.

POWER SUPPLIES
Power op amps do not require regulated supplies. However,
the worst-case output power is determined by the low-line
supply voltage in the ripple trough. The worst·case power
dissipation is established by the average supply voltage with
high-line conditions. The loss in power output that can be
guaranteed is the square of the ratio of these two voltages.
Relatively simple off-line switching power supplies can provide voltage conversion, line isolation and 5-percent regulation while reducing size and weight.
The regulation against ripple and line variations can provide
a substantial increase in the power output that can be guaranteed under worst-case conditions. In addition, switching
power supplies can convert low-voltage power sources
such as automotive batteries up to regulated, dual, highvoltage supplies optimized for powering power op amps.

HEAT SINKING
A semiconductor manufacturer has no control over heat
sink design. Temperature rating can only be based upon
case temperature as measured at the center of the package
bottom. With power pulses of longer duration than 100 ms,

"Isostrate" insulating pads for four-lead TO-3 packages are
available from Power Devices, Inc. Thermal grease is not
required, and the insulators should not be reused.

4-15

•

....

~r---------------------------------------------------------------~

~

Definition of Terms
Thermal gradient feedback: The input offset voltage
change caused by thermal gradients generated by heating
of the output transistors, but not the package. This effect is
delayed by several milliseconds and results in increased
gain error below 100 Hz.
Output-current limit: The output current with a fixed output
voltage and a large input overdrive. The limiting current
drops with time once the protection circuitry is activated.
Power diSSipation rating: The power that can be dissipated for a specified time interval without activating the protection circuitry. For time intervals in excess of 100 ms, dissipation capability is determined by heat sinking of the IC package rather than by the IC itself.
Thermal resistance: The peak, junction-temperature rise,
per unit of internal power diSSipation, above the case temperature as measured at the center of the package bottom.

Input offset voltage: The absolute value of the voltage
between the input terminals with the output voltage and current at zero.
Input bias current: The absolute value of the average of
the two input currents with the output voltage and current at
zero.
Input offset current: The absolute value of the difference
in the two input currents with the output voltage and current
at zero.
Common-mode reJection: The ratio of the input voltage
range to the change in offset voltage between the extremes.
Supply-voltage rejection: The ratio of the specified supply-voltage change to the change in offset voltage between
the extremes.
Output saturation threshold: The output swing limit for a
specified input drive beyond that required for zero output. It
is measured with respect to the supply to which the output is
sWinging.

The dc thermal resistance applies when one output transistor is operating continuously. The ac thermal resistance applies with the output transistors conducting alternately at a
high enough frequency that the peak capability of neither
transistor is exceeded.
Supply current: The current required from the power
source to operate the amplifier with the output voltage and
current at zero.

Large signal voltage gain: The ratio of the output voltage
swing to the differential input voltage required to drive the
output from zero to either Swing limit. The output swing limit
is the supply voltage less a specified quasi-saturation voltage. A pulse of short enough duration to minimize thermal
effects is used as a measurement signal.

Equivalent Schematic (excluding active protection circuitry)
r-~~~------------~----~--~-'~--~---~

1

13

80~

RI6
1

RI
3k

R4
5k

+~W....--IOI

·014

01
IN

RI5
0.15

R2
3k

~~--r----+-~~-4-4--1--+-0UT
02

RI4

0.15

013

·output clamps: hFERlI
TUH/8704-29

4-16

~National

~ Semiconductor

LM621 Brushless Motor Commutator
General Description
The LM621 is a bipolar IC designed for commutation of
brush less DC motors. The part is compatible with both
three- and four-phase motors. It can directly drive the power
switching devices used to drive the motor. The LM621 provides an adjustable dead-time circuit to eliminate "shootthrough" current spiking in the power switching circuitry.
Operation is from a 5V supply, but output swings of up to
40V are accommodated. The part is packaged in an 1B-pin,
dual-in-line package.

Features
• Adjustable dead-time feature eliminates current spiking
• On-chip clock oscillator for dead-time feature

• Outputs drive bipolar power devices (up to 35 mA base
current) or MOSFET power devices
• Compatible with three- and four-phase motors ...
- Bipolar drive to delta- or V-wound motors
- Unipolar drive to center-tapped V-wound motors
- Supports 30- and 60-degree shaft position sensor
placements for three-phase motors
- Supports 90-degree sensor placement for four-phase
motors
II Directly interfaces to pulse-width modulator output(s)
via OUTPUT INHIBIT (PWM magnitude) and DIRECTION (PWM sign) inputs
• Direct interface to Hall sensors
II Outputs are current limited
• Undervoltage lockout

Connection Diagram

+5VOL~
(VCCl) -~~;;;;;;~~::r=~~~~~~
UNDER
DIRECTION
DEAD-TIME
ENABLE
CLOCK
TIMING

HSI
HS2
HS3
30/60
SELECT

LOGIC
GROUND

2

3
4

VOLTAGE
LOCKOUT

DEAD-TIME
GENERATOR

18

5-40 MOTOR SUPPLY
VOLTAGE (VCC2)

17

OUTPUT
INHIBIT

16

CURRENT
SINK OUT #1

15

CURRENT
SINK OUT #2

14

CURRENT
SINK OUT #3

13

CURRENT
SOURCE OUT #1

12

CURRENT
SOURCE OUT #2

11

CURRENT
SOURCE OUT #3

10

POWER
GROUND

5
6
7

COMMUTATION
DECODER
LOGIC

--

8

9

TL/H/8679-1

Order Number LM621N
See NS Package Number N18A

4-17

Absolute Maximum Ratings (See Notes)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
VCCI
VCC2
Logic Inputs (Note I)
Logie Input Clamp Current
Output Voltages
Output Currents

Operating Ambient Temperature Range
-40·C to + 85·C
LM621
-65·C to + 150·C
Storage Temperature Range
150·C
Junction Temperature

+7V
+45V
VCC1 +0.5V, -0.5V
20mA
+45V, -0.5V

2000V

ESD Susceptibility (Note 10)
Lead Temperature, N pkg.
(Soldering, 4 sec.)

260"C

Internally current limited

Electrical Characteristics (See Notes)
Parameter

Conditions

Typ

Tested
Limits

Design
Limits

Units

2.0
2.0

2.0
2.0

V min
V min

DECODER SECTION
High Level Input Voltage
HSI, HS2, HS3:
30/60 SELECT:
High Level Input Current
HSI, HS2, HS3:
30/60 SELECT:

VIH = VCCI
VIH = VCCI

100
120

200
240

p.Amax
p.Amax

Low Level Input Voltage
HS1, HS3 and HS2
HS1, HS3 and HS2
30/60 Select

30/60 = 5V
30/60 = OV
HSI = HS3 = 5V

0.6
0.6
0.6

0.4
0.4
0.4

V max
V max
Vmax

Low Level Input Current
HSI and HS3:
HS2:
30/60 SELECT

VIL = 0.35V
VIL = 0.4V
VIL = O.OV

-400
-100
-700

-800
-200
-1000

p.Amax
p.Amax
p.Amax

Input Clamp Voltage
(Pins 2, 3, 5, 6, 7, 8, 17)

Iln=lmA
lin = -1 mA

Output Leakage Current
Sinking Outputs
Sourcing Outputs

Outputs Off
VCC2 = 40V,
VOUT = 40V
VOUT = OV

Shorl·Circuit Current
Sinking Outputs
Sourcing Outputs

VCC2 = 10V,
VOUT = 10V
VOUT = OV

50

35

mAmin

-50

-35

mAmin

Vsat (sinking)
Vdrop (sourcing) = (VCC2 - VOUT)

1= 20mA
1= -20mA

0.83
1.7

Output Rise Time

(sourcing)
CL<10pF

50

ns

Output Fall Time

(sinking)
CL:;; 10 pF

50

ns

Propagation Delay
(Hall Input to Output)

Dead·Time Off

200

ns

V
V

(VCCI + 0.7)
(-0.6)

4·18

0.2

1.0

p.A

-0.2

-1.0

p.A

1.00
2.00

V max
V max

Electrical Characteristics (See Notes) (Continued)
Parameter

Tested
Limits

Design
Limits

Units

2.0
2.0
2.0

2.0
2.0
2.0

Vmin
V min
V min

Pin 3 = OV

100
60
200

150
100
300

",A max
",A max
",A max

Pin 3 = OV

0.6
0.6
0.3

0.4
0.4
0.2

V max
V max
V max

Yin = 0.6V

-100
-60
-200

-150
-100
-300

",A max
",A max
",A max

Conditions

Typ

DEAD·TIME SECTION
High Level Input Voltage
DIRECTION:
OUTPUT INHIBIT:
DEAD-TIME ENABLE:

Pin3 = OV
Pin 17 = OV

High Level Input Current
DIRECTION:
OUTPUT INHIBIT:
DEAD-TIME ENABLE:

Yin = 5V

Low Level Input Voltage
DIRECTION:
OUTPUT INHIBIT:
DEAD-TIME ENABLE:
Low Level Input Current
DIRECTION:
OUTPUT INHIBIT:
DEAD-TIME ENABLE:

Yin = 0.6V
Yin = OV

Propagation Delays
(Inputs to Outputs)
OUTPUT INHIBIT
DIRECTION

Dead-Time Off,
(Pin 3 = OV)

Minimum Clock Period,
T CLK (Notes 3, 11)

200
200

ns
ns

R=11kn,Rl=1k
C = 200pF

1.8

"'s

Clock Accuracy
f = 100 kHz (Note 11)

R = 30k,Rl = lk
C=420pF

±3

%

Minimum Dead-Time
Minimum Dead-Time

Dead-Time Off
Dead-Time On

15
2

TCLK

ns

COMPLETE CIRCUIT
Total Current Drains

Outputs Off
15

10
22

30

mAmin
mAmax

3

2
6

9

mAmin
mAmax

3.6

3.0

ICCl
ICCl
VCC2 = 40V

ICC2
ICC2
Undervoltage Lockout
VCCl

Nole 1. Unless otherwise noted ambient temperature (TN

~

VMAX

25'C.

+ 5.0V, "recommended operating range VCC ~ 4.5V to 5.5V" VCC2 ~ + 10.0V, ambient temperature ~ 25"C.
Nole 3. The clock period Is typically TCLK ~ (0.756 x 10- 3) (R + I) C, where TCLK is in p.s, R Is in kO, and C Is pF. Also see selection graph in Typical
Note 2. Unless otherwise noted: VCCI

~

Characteristics for determining values of Rand C. Note that the value of R should be no less than 11 kO and C no less than 200 pF.
Nole 4. Tested limits are guaranteed and 100% production tested.
Nole 5. Design limits are guaranteed (but not 100% production tested) at the indicated temperature and supply voltages. These limits are not used to calculate
outgoing quality levels.
Nole 6. Specifications in boldface apply over junction temperature range of - 40"C to
Nole 7. Typical Thermal Resistances

+ B5'C.

OJA (see Note B):

N pkg, board mounted

IIO"C/W

N pkg, socketed

I1B'C/W

Note 8. Package thermal resistance indicates the ability of the package to dissipate heat generated on the die. Given ambient temperatura and power dissipation,
the thermal resistance parameter can be used to determine the approximate operating junction temperature. Operating junction temperature direcUy effects
product performance and reliability.

Nole 9. This part specifically does not have thermal shutdown protection to avoid safety problems related to an unintentional restart due to thermal time constant
variations. Care should be taken to prevent excessive power dissipation on the die.
Nole 10: Human body model, 100 pF, discharged through a 15000 resistor.
Nole 11: Rl

~

0 for C :<: 620 pF.

4-19

~

C'I

I

,------------------------------------------------------------------------------------------,
Typical Performance Characteristics

....I

Selection Graph
forRandC

Supply Currents
vs Temperature

Supply Currents
vs Temperature

60

- --

R=5Ik./

50
40

/

30

V

20

o
o

R=10k

14

V ~

~~~
400

-

800

r- rr-

16
15

~

13

V , / I--'" ;pc

/

10

17

IA

12
II
10

1200

1600

(HlcH =H3=5V
-50 -25 0

C(pf)

Vsat vs Temperature
1.0 0

~>~
_

-50 -25 0

e
>v

Vdrop vs Temperature

Typ. Vaat VS lout sink
Typ. Vdrop VS lout source
(@TA = 2S0C)
3.0

1\
i'

0.80

.......

-

r-

,

-50 -25 0

.......

25 50 75 100 125

2.5

"

2.00

~

1.80

~

1'\

!;

,:>

,

Jl

25 50 75 100 125
TEMpOC

2.20

......,

\
0.90

25 50 75 100 125

TEMp·C

>

l

';:'=20mA

1.60

~

f.L.

1.40
-50 -25 0

TEMP °C

-- -

2.0

"-1'\

25 50 75 100 125

TEWP °C

~

1.5

1.0

.r
0.5
o

o

-

10

,a'

r-

20

30

~

40

50

60

mA
TL/H/8679-2

Description of Inputs and Outputs
Pin 1: VCC1 (+ SV). The logic and clock power supply pin.

Pin 10: POWER GROUND. Ground for the output buffer
supply.

Pin 2: DIRECTION. This input determines the direction of
rotation of the motor; ie., clockwise vs. counterclockwise.
See truth table.
Pin 3: DEAD-TIME ENABLE. This input enables or disables
the dead-time feature. Connecting +5V to pin 3 enables
dead-time, and grounding pin 3 disables it. Pin 3 should not
be allowed to float.

Pins 11 thru 13: SOURCE OUTPUTS. The three currentsourcing outputs which drive the external power devices
that drive the motor.
Pins 14 thru 16: SINK OUTPUTS. The three current-sinking
outputs which drive the external power devices that drive
the motor.
Pin 17: OUTPUT INHIBIT. This input disables the LM621
outputs. It is typically driven by the magnitude signal from an
external sign/magnitude PWM generator. Pin 17 = +5V =
outputs off.

Pin 4: CLOCK TIMING. An RC network connected between
this pin and ground sets the period of the clock oscillator,
which determines the amount of dead-time. See Figure 2
and text.
Pins S thru 7: HS1, HS2, and HS3 (Hall-sensor Inputs).
These inputs receive the rotor-position sensor inputs from
the motor. Three-phase motors provide all three signals;
four phase motors provide only two, one of which is connected to both HS2 and HS3.
Pin 8: 30/60 SELECT. This input is used to select the required decoding for three-phase motors; ie, either "30-degree" (+ SV) or "60-degree" (ground). Connect pin 8 to
+ 5V when using a four-phase motor.
Pin 9: LOGIC GROUND. Ground for the logic power supply.

Pin 18: VCC2 (+S to +40V). This is the supply for the
collectors of the three current-sourcing outputs (pins 11 thru
13). When driving MOSFET power devices, pin 18 may be
connected to a voltage source of up to + 40V to achieve
sufficient output swing for the gate. When driving bipolar
power devices, pin 18 should be connected to + 5V to minimize on-chip power dissipation. Undervoltage lockout automatically shuts down all outputs if the VCC1 supply is too
low. All outputs will be off if VCC1 falls below the undervoltage lockout voltage.

4-20

LM621 Commutation Decoder Truth Table, which shows
both the 30- and 60-degree phasings (and the 90-degree
phasing for four-phase motors) and their required decoder
logic truth tables, respectively. Table I shows the phasing
(or codes) of the Hall-effect sensors for each 60-degree
(electrical) position range of the rotor, and correlates these
data to the commutator sink and source outputs required to
drive the power switches. These phasings are common to
several motor manufacturers. The 60-degree phasing is preferred to 30-degree phasing because the all-zeros and allones codes are not generated. The 60-degree phasing is
more failsafe because the all-zeros and all-ones codes
could be inadvertently generated by things like disconnected or shorted sensors.
Because the above terminology is not used consistently
among all motor manufacturers, Table II, Alternative Sensor-phasing Names, will hopefully clarify some of the differences. Table II shows a different 60-degree phasing, and
120-,240-, and 300-degree phasings. Comparison with Table I will show that these four phasings are essentially shifted and/or reversed-order versions of those used with the
LM621.
Figure 1 shows the waveforms associated with the commutation decoder logic for a motor which has 60-degree rotorposition phasing, along with the generated motor-drive
waveforms. As can be seen in the drawing, Hall-effect sensor Signals HS1 through HS3 are separated by 60 electrical
degrees, which is the required angular resolution for threephase motors.

Functional Description
The commutation decoder receives Hall-sensor inputs HS1,
HS2, and HS3 and a 30/60 SELECT input. This block decodes the gray-code sequence to the required motor-drive
sequence.
The dead-time generator monitors the DIRECTION input
and inhibits the outputs (pins 11 thru 16) for a time sufficient
to prevent current-spiking in the external power switches
when the direction is reversed.
The six chip outputs drive external power switching devices
which drive the motor. Three outputs source current; the
remaining three sink current. The output transistors provide
up to 50 mA outputs for driving devices, or up to 40V output
swings for driving MOSFETs. The LM621 logic is powered
from 5V.
The undervoltage lockout section monitors the Vee supply
and if the voltage is not sufficient to permit reliable logic
operation, the outputs are shutdown.

Three-Phase Motor Commutation
There are two popular conventions for establishing the relative phasing of rotor-position signals for three-phase motors. While usually referred to as 30-degree and 60-degree
sensor placements, this terminology refers to mechanical
degrees of sensor placement, not electrical degrees. The
electrical angular resolution is the required 60 degrees in
both cases. The phasing differences can be noted by comparing the sequences of HS1 through HS3 entries in Table I,
ROTOR POSmON:
(ELEC. DEGREES)

0

DIRECTION INPUT:

1
0
1 '
0-'
1
0
1 I

HALL-SENSOR
INPUTS

r"

HS2'
•

HS3:

SINK 1:
SINK 2:
SINK 3:

,
,

SOURCE 2:
SOURCE 3:

120

180

240

300

I

I

, , Ll
I

I

I

I

Your
GND
Vour
GND
Vour
GND

I

I

I

I

I

I

I

I

"~
~'II'
~
I
I
I
I
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I
I
~"

" " " " ",
I

I

I

I

,.............
I

I

I

~
----a' "
........

I

180

240

300

I

360

I

, REVERSE

I

I

r----------;

L.......L.-J

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:-l

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,

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,
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L....I..
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r--I
, ......----.-; ,
J...-.J
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L....I..
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III~'

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,
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r--:--l~~--~~--~
,

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~-

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't;'1"
--1

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w--~

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~::
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,--,
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r--,
t---;---f
:

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,
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13
12

•

11

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:r,
r--,
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II~'I

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t-_ I,

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...........

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15

r:-l
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.t--.---tI

+1 ' , , r7'I
o ,--'

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L..:-,J--,

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6

7

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,~,

+,
O I

Lt.l621
PIN
NUMBERS
2

I

o .,

-

120

5

,

I

VCC2
VSAT
VCC2
VSAT
VCC2
VSAT

60

I

o~
,
I

o

, FORWARD,

+~:::
MOTOR
DRIVE
CURRENTS

360

I

,

OUTPUTS
SOURCE 1:

60

l_-W-J',

I~III

I

'

,
I

I

I

TL/H/8679-6

FIGURE 1. Commutation Waveforms for 60-degree Phasing

4-21

,..
N
CD

::i

Three-Phase Motor Commutation

..J

(Continued)

TABLE I. LM621 Commutation Decoder Truth Table
Sensor
Phasing

30deg

60deg

90deg

Position
Range

Sensor Inputs

Sink Outputs

Source Outputs

HS1

HS2

HS3

1

2

3

1

2

3

0-60
60-120
120-180
180-240
240-300
300-360

0
0
0
1
1
1

0
0
1
1
1
0

0
1
1
1
0
0

ON
ON
off
off
off
off

off
off
ON
ON
off
off

off
off
off
off
ON
ON

off
off
off
ON
ON
off

ON
off
off
off
off
ON

off
ON
ON
off
off
off

0-60
60-120
120-180
180-240
240-300
300-360

1
1
1
0
0
0

0
0
1
1
1
0

1
0
0
0
1
1

ON
ON
off
off
off
off

off
off
ON
ON
off
off

off
off
off
off
ON
ON

off
off
off
ON
ON
off

ON
off
off
off
off
ON

off
ON
ON
off
off
off

0-90
90-180
180-270
270-360

0
0
1
1

1
0
0
1

HS2
HS2
HS2
HS2

off
ON
off
off

na
na
na
na

off
off
ON
off

off
off
off
ON

na
na
na
na

ON
off
off
off

5

6

7

16

15

14

13

12

11

Pin Numbers:

Note 1: The above outputs are generated when the Direction Input, pin 2, Is logic high. For reverse rotation (pin 2 logic low), the above sink and source output
states become exchanged.
Note 2: For four·phase motors sink and source outputs number two (pins 15 and 12) are not used; hense the "na" (not applicable) In the appropriate columns
above. F/{JUT6 6 shows how the required sink and source outputs for four·phase motors are derived.

TABLE II. Alternative Sensor-Phasing Names
Alternate
Phasing

"60deg"

"120deg"

"240 deg"

"300deg"

Position
Range

HS1

Sensor Inputs
HS2

HS3

0-60
60-120
120-180
180-240
240-300
300-360

0
1
1
1
0
0

0
0
1
1
1
0

0
0
0
1
1
1

Same as 30·degree phasing, but in reverse
order; i.e., only change is relative direction.

0-60
60-120
120-180
180-240
240-300
300-360

0
1
1
1
0
0

0
0
0
1
1
1

1
1
0
0
0
1

Same as 60·degree phasing. but with shifted
order of position ranges; i.e., only change is
relative phasing of sensor signals.

0-60
60-120
120-180
180-240
240-300
300-360

0
1
1
1
0
0

1
1
0
0
0
1

0
0
0
1
1
1

Same comment as above for "120 deg"
phaSing.

0-60
60-120
120-180
180-240
240-300
300-360

0
1
1
1
0
0

1
1
1
0
0
0

1
1
0
0
0
1

Same as 30-degree phasing, but with shifted
order of position ranges, i.e., only change is
relative phasing of sensor signals.

Corresponding LM621 Position
Range and/or Comments

Four-Phase Motor Commutation
Four·phase motors use a 90·degree (quadrature) rotor-position sensor phasing. This phasing scheme is also shown in
Table I. LM621 Commutation Decoder Truth Table. As
shown in Table I, the 90·degree phasing has only two rotor-

position·sensor signals. HS1 and HS2. When using the
LM621 to run a four-phase motor the HS2 signal is connected to both the HS2 and HS3 chip inputs.

4·22

,-----------------------------------------------------------------------------, r

a:::

Dead-Time Feature
The DEAD-TIME ENABLE input is used to enable this feature (by connecting + 5V to pin 3). The reason for providing
this feature is that the external power switches are usually
totem-pole structures. Since these structures switch heavy
currents, if either totem-pole device is not completely turned
off when its complementary device turns on, heavy "shootthrough" current spiking will occur. This situation occurs
when the motor DIRECTION input changes (when all output
drive polarities reverse), at which time device turn-off delay
can cause the undesired current spiking.

the graph in Typical Peformance Characteristics, the time of
one clock period (in p.s) is approximately (0.756 X 10- 3)
(R + 1) C, where R is in kO and C is in pF; the period can
be measured with an oscilloscope at pin 4. The dead-time
generator function monitors the DIRECTION input for
changes, synchronizes the direction changes with the internal clock, and inhibits the chip outputs for two clock periods.
Flip-flops FF1 through FF3 form a three-bit, shift-register
delay line, the input of which is the DIRECTION input. The
flip-flops are the only elements clocked by the internal clock
generator. The shift register outputs must all have the same
state in order to enable gate G1 or G2, one of which must
be enabled to enable the chip outputs. As soon as a direction change input is sensed at the output of FF1, gates G1
and G2 will be disabled, thereby disabling the drive to the
power switches for a time equal to two clock periods.

Figure 2 shows the logic of the dead-time generator. The
dead-time generator includes an RC oscillator to generate a
required clock. Pin 4 (CLOCK TIMING) is used to connect
an external RC network to set the frequency of this oscillator. The clock frequency should be adjusted so that two
periods of oscillation just slightly exceed the worst-case
turn-off time of the power switching devices. As shown by

~

....

DIRECTIONIJ-_ _ _ _ _...- - - - - - - - - - - - - - - - - - - - - _ -.....
(2)
DIR
CLOCK
TIMING
Rl
...-..........."t/lro{]--I4
CLOCK
GENERATOR

C

DEAD-TIME
ENABLE
(3)
OUTPUT
INHIBIT I J - - - - i .;~-----------------------I

)---1-...

....-'

(17)

OE

TO
COMMUTATION
DECODER

FIGURE 2. Dead-Time Generator Logic Diagram

"1
CLOCK

r- TOLK

I I I I I I I I I I IS 5 I I I I I I I I I I I I I I I I

-jlI '-'~

Sl

m-Q _____~I

S5

DIRECTION _ _ _ _

Fr2-Q(DIR)

FF3-Q

TLlH/8879-7

1.....
1_________

II

_ _ _ _ _+-".----5 5

-------1-.. . .

s

OE~S

-I

I- DEAD TIME
TL/H/8679-6

FIGURE 3. Dead-Time Generator Waveforms

4-23

overcurrent sensing circuit are also detailed in Figure 4. This
application example assumes a device turn-off time of about
4.8 /Ls maximum, as evidenced by the choice of Rand C.
See Typical Performance Characteristics. The choice of RC
should be made such that two periods are at least equal to
the maximum device turn-off time.

Dead·Time Feature (Continued)
Dead-time is defined as the time the outputs are blanked off
(to prevent shoot-through currents) after a direction change
input. See Figure 3. It can be seen that the dead-time is two
clock periods. Since the dead-time scheme introduces delay into the system feedback control loop, which could impact system performance or stability, it is important that the
dead-time be kept to a minimum. From Figure 3 it can be
seen that the time between a direction change signal and
the initiation of output blanking can vary up to one clock
period due to asynchronous nature of the clock and the
direction signal.

The choice of the value for Rlimit (the resistors which couple
the LM621 outputs to the power switches) depends on the
input current requirements of the power switching devices.
These resistors should be chosen to provide only the
amount of current needed by the device inputs, up to 50 mA
(typical). The resistors minimize the dissipation incurred by
the LM621. Although Figure 4 shows the 5-40V supply (pin
18) connected to the motor supply voltage, this was done
only to emphasize the ability of the part to provide up to 40V
output swings. For the bipolar power switches shown, connecting pin 18 to a 5V supply would reduce on-chip power
dissipation. Driving FET power switches, however, may require connecting pin 18 to a higher voltage. Figure 5 is the
three-phase application built with MOSFET power-switching
components. Note that since the output Vdrop (sourcing) is
at least 1.5V, VCC2 can be chosen to avoid overdriving the
MOSFET gates.

Typical Applications
THREE-PHASE EXAMPLES
Figure 4 is a typical LM621 application. This circuitry is for
use with a three-phase motor having 3~-degree sensor
phasing, as indicated by connection of the 30/60 SELECT
input, pin 8, to a logic "1" (+5V). The same connection of
the DEAD-TIME ENABLE input, pin 3, enables this feature.
Typical power switches and a simple implementation of an

RUMIT (X6)

~

18
+5 VOLTS

MOTOR
SUPPLY
VOLTAGE
(5-40V)

SINK:
16

DEAD-TIME
ENABLE
30/60 SELECT

POWER SWITCHES

I

lK

#/1

I
I

•

I

3
8

= 1 ktl.

II,

.....+-'VV'v--l4

13
SOURCE

LM621
BRUSHLESS
MOTOR
COMMUTATOR

SINK
15

C=

#/2

200pr

.........---19

•

12
SOURCE.
I

••

DIR
SIGN - - - - - - - 1 2

SINK:

a
#/3

. . . - - - - -.... 5
. . . - - - -..... 6

.------17

rROM
PULSE
WIDTH
MAG
MODULATOR

11
SOURCE

I
I
I
I

oj>C

I

ROTOR POSITION
SENSORS

-+...............

HSl
HS2
HS3
TlIH/8679-9

FIGURE 4. Commutation of Three-Phase Motor (Bipolar Switches)

4-24

r-

Typical Applications

s:

G)

(Continued)

~

.....
POWER SWITCHES
MOTOR
SUPPLY
VOLTAGE

18
+5 VOLTS

SINK
16

DEAD-TIME
ENABLE
3D/50 SELECT

lK

#1
3
8

Rl = lK

4
R = 11K

SOURCE

I

SINK
15

C=
200 pF

--

#2
9

DIR

SIGN

13
LM621
BRUSHLESS
MOTOR
COMMUTATOR

-------1 2

12

SINK
141--~"""~-I

cl>C

#3

11 1---++-+--1
ROTOR POSITION
SENSORS

FROM
PULSE
WIDTH
MAG -IH-4--4
MODULATOR

HSI
HS2
HS3

.. ------------TUH/8679-10

FIGURE 5. Commutation of Three-Phase Motor (MOSFET Switches)

4·25

5

:5

r-------------------------------------------------------------------------~

Typical Applications (Continued)
FOUR-PHASE EXAMPLE
Figure 6 is typical of the circuitry used to commutate a fourphase motor using the LM621. This application is seen to
differ from the three-phase application example in that the
LM621 outputs are utilized differently. Four-phase motors
require four-phase power switches, which in turn require'the
commutator to provide four current-sinking outputs and four
current sourcing outputs. The la-pin package of the LM621
facilitates only three sinking and three sourcing outputs. The
schematic shows the 30/60 SELECT input in the 30-degree
select state (pin a high) and rotor-position sensor inputs
HS2 and HS3 connected, together. This connection truncates the number of possible rotor-position input states to
four, which is consistent with the 90-degree quadrature rotor-position Signals provided by four-phase motors. With the
L~621 outputs connected as shown, this approach provides the needed power-switch drive Signals for a fourphase motor. Note that only four of the six LM621 outputs

(SINK #1 and #3, and SOURCE #1 and #3) are used
directly, and that these are also inverted to form the remaining four. SINK #2 and SOURCE #2 outputs are not used.
HALF-WAVE DRIVE EXAMPLE
The previous applications examples involved delta-configured motor windings and full-wave operation of the motor.
The application shown in Figure 7 differs in that it features
half-wave operation of a motor with the windings in a Y-configuration. This approach is suitable for automotive and other applications where only low-voltage power supplies are
conveniently available. The advantage of this power-switching scheme is that there is only one switch-voltage drop in
series with the motor winding, thereby conserving more of
the available voltage for application to the motor winding.
Half-wave operation provides only unidirectional current to
the windings; in contrast to the bidirectional currents applied
by the previous full-wave examples.

+5 VOLTS

B+

18
DEAD-TIME
ENABLE
30/60 SELECT

SINK #1
16
LM621 15

lK

POWER SWITCHES
D-

: BRUSHLESS
MOTOR
COMMUTATOR

II, "

MOTOR
SUPPLY
VOLTAGE

SINK 2

lK

4

C+

fj>A
4-PHASE
BRUSHLESS
DC MOTOR

SINK #3
14

C"
200 pF

AD+
SOURCE #1
13

DIR
SIGN

2
HSI
HS2
HS2

5
6

7

12
11
SOURCE #3

NC

ROTOR POSITION
SENSORS

FROM
PULSE
MAG
WIDTH
MODULATOR

I::==================!:J-I----I'"
FIGURE 6. Commutation of Four-Phase Motor

4-26

TLlH/8879-11

Typical Applications (Continued)
+5 VOLTS

MOTOR SUPPLY VOLTAGE

.--------- ---------

18

DEAD-TIME
ENABLE

1K

I}
I

5
6
7

HS1
HS2
HS3

::

} NC

ROTOR
POSITION

3-PHASE
Y-CONfIGURED
MOTOR

LM621
BRUSHLESS
MOTOR
COMMUTATOR
CLOCK TIMING
C

14
3D/SO SELECT ....- - - -....

SOURCE

#2

DIR

SIGN

}

-------1

POWER
SWITCHES

fROM
PULSE
WIDTH
MAG - - - - \
MODULATOR

TL/H/B679-12

FIGURE 7. Half-Wave Drive of V-Configured Motor

4-27

en ,----------------------------------------------------------------------------,
N

CD

:i..... ~National
~

~ Semiconductor

CD

:l LM628/LM629 Precision Motion Controller
General Description

Features

The LM628/LM629 are dedicated motion-control processors designed for use with a variety of DC and brush less DC
servo motors, and other servomechanisms which provide a
quadrature incremental position feedback signal. The parts
perform the intensive, real-time computational tasks required for high performance digital motion control. The host
control software interface is facilitated by a high-level command set. The LM628 has an 8-bit output which can drive
either an 8-bit or a 12-bit DAC. The components required to
build a servo system are reduced to the DC motor/actuator,
an incremental encoder, a DAC, a power amplifier, and the
LM628. An LM629-based system is similar, except that it
provides an 8-bit PWM output for directly driving H-switches.
The parts are fabricated in NMOS and packaged in a 28-pin
dual in-line package, and are offered in both 6 MHz and
8 MHz maximum frequency versions. The suffixes -6 and -8,
respectively, are used to designate version. They incorporate an SDA core processor and cells designed by SDA.

•
•
•
•
•
•
•
•
•
•
•

32-bit position, velocity, and acceleration registers
Programmable digital PID filter with 16-bit coefficients
Programmable derivative sampling interval
8- or 12-bit DAC output data (LM628)
8-bit sign-magnitude PWM output data (LM629)
Internal trapezoidal velocity profile generator
Velocity, target position, and filter parameters may be
changed during motion
Position and velocity modes of operation
Real-time programmable host interrupts
8-bit parallel asynchronous host interface
Quadrature incremental encoder interface with index
pulse input

Lt,1628
HOST I/O PORT

t--I+--,'<--+ TO HOST PROCESSOR

TlIH/9219-1

FIGURE 1. Typical System Block Diagram

Connection Diagrams
LM628

LM629

iii

1

28

A

2

27

B

3

voo
iiST

iii

28

A

27

Voo
iiST

26

ClK

8

26

CLK

07

25

DACO

07

25

NC

06

24

DACI

24

NC

os

23

DAC2

os

23

Ne

D4

22

DAC3

04

22

He

D3

8

21

DAC4

D3

21

Ne

02

9

20

DAC5

02

20

Ne

01

10

19

DAC6

01

19

PWM MAG

DO

11

18

DAC7

00

18

PWM SIGN

cs

12

17

HI

cs

17

HI

jjjj

13

16

13

16

14

15

PS
Viii

jjjj

GNO

GNO

14

15

PS
Viii

TL/H/9219-2

TlIH/9219-3

Order Number LM628N-6, LM628N-8, LM629N-6 or LM629N-8
See NS Package Number N28B
4-28

Absolute Maximum Ratings

Operating Ratings

(Note 1)

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Voltage at Any Pin with
Respect to GND (Pin 14)

< TA <

+85'C

< fCLK < 6.0 MHz
< fCLK < 8.0 MHz
4.5V < VDD < 5.5V

1.0 MHz
1.0 MHz

VDDRange

- 65'C to + 150'C

Lead Temperature (Soldering, 4 sec.)
Maximum Power Dissipation
ESD Tolerance
(CZAP = 120 pF, RZAP

Clock Frequency:
LM628N·6, LM629N·6
LM628N·8, LM629N·8

-0.3Vto +7.0V

Ambient Storage Temperature

-40'C

Temperature Range

260'C
550mW

= 1.5k)

2000V

DC Electrical Characteristics (VDD and TAper Operating Ratings; fCLK = 6 MHz)
Symbol

Parameter

Conditions

Tested Limits
Min

Supply Current

IDD

Outputs Open

Units

Max
100

mA

INPUT VOLTAGES
VIH

Logic 1 Input Voltage

VIL

Logic 0 Input Voltage

liN

Input Currents

2.0

0';;; VIN';;; VDD

-10

IOH

2.4

-10

V
0.8

V

10

/LA

OUTPUT VOLTAGES

VOL

Logic 0

= -1.6mA
IOL = 1.6mA

lOUT

TRI·STATE® Output Leakage Current

0';;; VOUT';;; VDD

VOH

Logic 1

V
0.4

V

10

/LA

AC Electrical Characteristics
(VDD and TAper Operating Ratings; fCLK = 6 MHz; CLOAD = 50 pF; Input Test Signal tr = tf = 10 ns)
Timing Interval

Tested Limits

T#
Min

Units
Max

ENCODER AND INDEX TIMING (See Figure 2)
Motor·Phase Pulse Width

Tl

-

16

-

8

fCLK

Dwell·Time per State

T2

fCLK

Index Pulse Setup and Hold
(Relative to A and BLow)

/Ls
/Ls

T3

0

p.s

Clock Pulse Width
LM628N·6 or LM629N·6
LM628N·8 or LM629N·8

T4
T4

78
57

ns
ns

Clock Period
LM628N·6 or LM629N·6
LM628N·8 or LM629N·8

T5
T5

166
125

ns
ns

Reset Pulse Width

T6

-

CLOCK AND RESET TIMING (See Figure 3)

8

fCLK

4·29

p.S

AC Electrical Characteristics

(Continued)
(VDD and TAper Operating Ratings; fCLK = 6 MHz; CLOAD = 50 pF; Input Test Signal tr = tf = IOns)
Timing Interval

Tested Limits

T#
Min

Units
Max

STATUS BYTE READ TIMING (See Figure 4)
Chip-Select Setup/Hold Time

T7

0

ns

Port-Select Setup Time

T8

30

ns

Port-Select Hold Time

T9

30

Read Data Access Time

Tl0

Read Data Hold Time

Til

RD High to Hi-Z Time

T12

ns
180

0

ns
ns

180

ns

COMMAND BYTE WRITE TIMING (See Figure 5)
Chip-Select Setup/Hold Time

T7

0

ns

Port-Select Setup Time

T8

30

ns

Port-Select Hold Time

T9

30

ns
(Note 2)

Busy Bit Delay

T13

WR Pulse Width

T14

100

ns
ns

Write Data Setup Time

T15

50

ns

Write Data Hold Time

T16

120

ns

DATA WORD READ TIMING (See Figure 6)
Chip-Select Setup/Hold Time

T7

0

ns

Port-Select Setup Time

T8

30

ns

Port-Select Hold Time

T9

30

Read Data Access Time

Tl0

ns
180

0

ns

Read Data Hold Time

Til

RD High to Hi-Z Time

T12

180

ns

Busy Bit Delay

T13

(Note 2)

ns

Read Recovery Time

T17

ns

120

ns

DATA WORD WRITE TIMING (See Figure 7)
Chip-Select Setup/Hold Time

T7

0

ns

Port-Select Setup Time

T8

30

ns

Port-Select Hold Time

T9

30

Busy Bit Delay

T13

WR Pulse Width

T14

100

ns

Write Data Setup Time

TI5

50

ns

Write Data Hold Time

TI6

120

ns

ns
(Note 2)

ns

Write Recovery Time
TI8
120
ns
Nate 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. DC and AC electrical specifications do not apply when operating
the device beyond the above Operating Ratings.
Nate 2: In order to read the busy bit, the stetus byte must first be read. The time required to read the busy bit far exceeds the time the chip requires to set the busy
bit. It is, therefore, impossible to test actual busy bit delay. The busy bit is guaranteed to be valid as soon as the user is able to read it.

4-30

l

I-n

'I'

n--j

A-.J
~I: 1J~T2~
I-T2
8_--,1
L
1

1

I-T3--1

I-T3-1

-;

; - - INDEX=A·fj·IN

TL/H/9219-4

FIGURE 2. Quadrature Encoder Input Timing

CLOCK
I-T4-+-T4~-- T5--.J

I---T6

-----I

TLlH/9219-5

FIGURE 3. Clock and Reset Timing

rDO-D7

______________ !'l!!
(HI-Z)

T12

DATA
VALID
TL/H/9219-6

FIGURE 4. Status Byte Read Timing

4·31

cs

PS
T14

Viii

VDf
VIL

DO-D7

BUSY
BIT

TlIH/9219-7

FIGURE 5. Command Byte Write Timing

j-T13
BUSY

BIT

TlIH/9219-B

FIGURE 6. Data Word Read Timing

DO-D7

BIT ______________________________________________________________~
BUSY
TL/H/9219-9

FIGURE 7. Data Word Write Timing

4·32

r-

s:
0"1

Pinout Description (See Connection Diagrams)

N

Pin I, Index (iN) Input: Receives optional index pulse from
the encoder. Must be tied high if not used. The index position is read when Pins 1, 2, and 3 are low.

2. LM628 (12-bit output mode): Outputs two, multiplexed
6-bit words. The less-significant word is output first. The
MSB is on Pin 18 and the LSB is on Pin 23. Pin 24 is used
to demultiplex the words; Pin 24 is low for the less-significant word. The positive-going edge of the signal on Pin
25 is used to strobe the output data. Figure 8 shows the
timing of the multiplexed signals.

Pins 2 and 3, Encoder Signal (A, B) Inputs: Receive the
two-phase quadrature signals provided by the incremental
encoder. When the motor is rotating in the positive ("forward") direction, the signal at Pin 2 leads the signal at Pin 3
by 90 degrees. Note that the signals at Pins 2 and 3 must
remain at each encoder state (See Figure 9) for a minimum
of 8 clock periods in order to be recognized. Because of a
four-to-one resolution advantage gained by the method of
decoding the quadrature encoder signals, this corresponds
to a maximum encoder-state capture rate of 1.0 MHz (fCLK
= 8.0 MHz) or 750 kHz (fCLK = 6.0 MHz). For other clock
frequencies the encoder signals must also remain at each
state a minimum of 8 clock periods.

3. LM629 (sign/magnitude outputs): Outputs a PWM sign
signal on Pin 18, and a PWM magnitude signal on Pin 19.
Pins 20 to 25 are not used in the LM629. Figure 11 shows
the PWM output signal format.
Pin 26, Clock (ClK) Input: Receives system clock.
Pin 27, Reset (RSn Input: Active-low, positive-edge triggered, resets the LM628 to the internal conditions shown
below. Note that the reset pulse must be logic low for a
minimum of 8 clock periods. Reset does the following:

Pins 4 to II, Host I/O Port (DO to D7): Bi-directional data
port which connects to host computer/processor. Used for
writing commands and data to the LM628, and for reading
the status byte and data from the LM628, as controlled by
CS (Pin 12), PS (Pin 16), RD (Pin 13), and WR (Pin 15).

1. Filter coefficient and trajectory parameters are zeroed.
2. Sets position error threshold to maximum value (7FFF
hex), and effectively executes command LPEI.
3. The SBPAlSBPR interrupt is masked (disabled).
4. The five other interrupts are unmasked (enabled).

Pin 12, Chip Select (CS) Input: Used to select the LM628
for writing and reading operations.

5. Initializes current position to zero, or "home" position.

Pin 13, Read (RD) Input: Used to read status and data.
Pin 14, Ground (GND): Power-supply return pin.

6. Sets derivative sampling interval to 2048/fCLK or 256 p.s
for an 8.0 MHz clock.

Pin 15, Write (WR) Input: Used to write commands and
data.

7. DAC port outputs 800 hex to "zero" a 12-bit DAC and
then reverts to 80 hex to "zero" an 8-bit DAC.

Pin 16, Port Select (PS) Input: Used to select command or
data port. Selects command port when low, data port when
high. The following modes are controlled by Pin 16:

Pin 17, Host Interrupt (HI) Output: This active-high signal
alerts the host (via a host interrupt service routine) that an
interrupt condition has occurred.

Immediately aiter releasing the reset pin from the LM628,
the status port should read '00'. If the reset is successfully
completed, the status word will change to hex '84' or 'C4'
within 1.5 ms. If the status word has not changed from hex
'00' to '84' or 'C4' within 1.5 ms, perform another reset and
repeat the above steps. To be certain that the reset was
properly performed, execute a RSTI command. If the chip
has reset properly, the status byte will change from hex '84'
or 'C4' to hex '80' or 'CO'. If this does not occur, perform
another reset and repeat the above steps.

Pins 18 to 25, DAC Port (DACO to DAC7): Output port
which is used in three different modes:

Pin 28, Supply Voltage (Voo): Power supply voltage
(+5V).

1. Commands are written to the command port (Pin 16 low),
2. Status byte is read from command port (Pin 16 low), and
3. Data is written and read via the data port (Pin 16 high).

1. LM628 (8-bit output mode): Outputs latched data to the
DAC. The MSB is Pin 18 and the LSB is Pin 25.
2048

SELECT:
(PIN 24)

STROBE:
(PIN 25)

==(

f----VI-I'- ' -X--f
J.----.!'
~H
~,:--j
eLK

DATA:
(PINS 18 - 23)

6 LOW BITS

~I_

-----\ l

BITS

I
f: 1-

'x

J ---I~
\; I

~

LK

~f~~K ~

TUH/9219-10

FIGURE 8. 12-Bit Multiplexed Output Timing

4-33

m

"r-

s:

0"1
N

CD

Theory of Operation
INTRODUCTION
The typical system block diagram (See Figure 1) illustrates
a servo system built using the LM628. The host processor
communicates with the LM628 through an 110 port to facilitate programming a trapezoidal velocity profile and a digital
compensation filter. The DAC output interfaces to an exlernal digital-to-analog converter to produce the signal that is
power amplified and applied to the motor. An incremental
encoder provides feedback for cloSing the position servo
loop. The trapezoidal velocity profile generator calculates
the required trajectory for either position or velocity mode of
operation. In operation, the LM628 subtracts the actual position (feedback position) from the desired position (profile
generator position), and the resulting position error is processed by the digital filter to drive the motor to the desired
position. Table I provides a brief summary of specifications
offered by the LM828/LM629:

and an index pulse input. The quadrature signals are used
to keep track of the absolute position of the motor. Each
time a logic transition occurs at one of the quadrature inputs, the LM628 internal position register is incremented or
decremented accordingly. This provides four times the resolution over the number of lines provided by the encoder.
See Figure 9. Each of the encoder signal inputs is synchronized with the LM628 clock.
The optional index pulse output provided by some encoders
assumes the logic-low state once per revolution. If the
LM628 is so programmed by the user, it will record the absolute motor position in a dedicated register (the index register) at the time when all three encoder inputs are logic low.
If the encoder does not provide an index output, the LM628
index input can also be used to record the home position of
the motor. In this case, typically, the motor will close a
switch which is arranged to cause a logic-low level at the
index input, and the LM628 will record motor position in the
index register and alert (interrupt) the host processor. Permanently grounding the index input will cause the LM628 to
malfunction.

POSITION FEEDBACK INTERFACE
The LM628 interfaces to a motor via an Incremental encoder. Three inputs are provided: two quadrature signal inputs,

TABLE I. System Specifications Summary
Position Range

-1,073,741,824 to 1,073,741,823 counts

Velocity Range

oto 1,073,741,823/216 counts/sample; ie, 0 to 16,383 counts/sample, with a resolution of 1/216
counts/sample.

Acceleration Range

oto 1,073,741,823/216 counts/sample/sample; ie, 0 to 16,383 counts/sample/sample, with a
resolution of 1/216 counts/sample/sample

Motor Drive Output

LM628: 8-bit parallel output to DAC, or 12-bit multiplexed output to DAC
LM629: 8-bit PWM sign/magnitude signals

Operating Modes

Position and Velocity

Feedback Device

Incremental Encoder (quadrature signals; support for index pulse)

Control Algorithm

Proportional Integral Derivative (PID) (plus programmable integration limit)

Sample Intervals

Derivative Term: Programmable from 2048lfCLK to (2048 • 256)lfcLK in steps of 2048lfCLK (256
to 65,536 I-£s for an 8.0 MHz clock).
Proportional and Integral: 2048lfCLK

4-34

Theory of Operation

.-s::
en
co
.......

(Continued)

I\)

.-s::

STAlES B A
1 1 0
pos
2 1 1
3 0 1
DIRECTION
400
1 1 0
NEG
2 1 1
3 0 1

1

en

I\)

CD

1

TlIH/9219-11

FIGURE 9. Quadrature Encoder Signals
\ ' LIMITING VELOCIlY
VELOCIlY

STOPPING POSITION
IS INTEGRAL or
TRAPEZOID

/
TIME

(a)

VELOCllY

TIME

(b)

TlIH/9219-12

FIGURE 10. Typical Velocity Profiles
VELOCITY PROFILE (TRAJECTORY) GENERATION

condition goes undetected, and the impeding force on the
motor is subsequently released, the motor could reach a
very high velocity in order to catch up to the desired position
(which is still advancing as specified). This condition is easily detected; see commands LPEI and LPES.
All trajectory parameters are 32-bit values. Position is a
signed quantity. Acceleration and velocity are specified as
16-bit, positive-only integers having 16-bit fractions. The integer portion of velocity specifies how many counts per
sampling interval the motor will traverse. The fractional portion designates an additional fractional count per sampling
interval. Although the position resolution of the LM628 is
limited to integer counts, the fractional counts provide increased average velocity resolution. Acceleration is treated
in the same manner. Each sampling interval the commanded acceleration value is added to the current desired velocity to generate a new desired velocity (unless the command
velocity has been reached).

The trapezoidal velocity profile generator computes the de·
sired position of the motor versus time. In the position mode
of operation, the host processor specifies acceleration,
maximum velocity, and final position. The LM628 uses this
information to affect the move by accelerating as specified
until the maximum velocity is reached or until deceleration
must begin to stop at the specified final position. The deceleration rate is equal to the acceleration rate. At any time
during the move the maximum velocity and/or the target
position may be changed, and the motor will accelerate or
decelerate accordingly. Figure 10 illustrates two typical trapezoidal velocity profiles. Figure 10 (a) shows a simple trapezoid, while Figure 10 (b) is an example of what the trajectory
looks like when velocity and position are changed at different times during the move.
When operating in the velocity mode, the motor accelerates
to the specified velocity at the specified acceleration rate
and maintains the specified velocity until commanded to
stop. The velocity is maintained by advancing the desired
position at a constant rate. If there are disturbances to the
motion during velocity mode operation, the long-time average velocity remains constant. If the motor is unable to
maintain the specified velocity (which could be caused by a
locked rotor, for example), the desired position will continue
to be increased, resulting in a very large position error. If this

One determines the trajectory parameters for a desired
move as follows. If, for example, one has a 500·line shaft
encoder, desires that the motor accelerate at one revolution
per second per second until it is moving at 600 rpm, and
then decelerate to a stop at a position exactly 100 revolutions from the start, one would calculate the trajectory parameters as follows:

4-35

Theory of Operation (Continued)
let P = target position (units = encoder counts)

a constant torque loading, the motor will still be able to
achieve zero position error.

let R = encoder lines • 4 (system resolution)
then R = 500 • 4 = 2000

The third term, the derivative term, provides a force proportional to the rate of change of position error. It acts just like
viscous damping in a damped spring and mass system (like
a shock absorber in an automobile). The sampling interval
associated with the derivative term is user-selectable; this
capability enables the LM628 to control a wider range of
inertial loads (system mechanical time constants) by providing a better approximation of the continuous derivative. In
general, longer sampling intervals are useful for low-velocity
operations.

and P = 2000 * desired number of revolutions
P = 2000 • 100 revs = 200,000 counts (value to
load)
P (coding) = 00030040 (hex code written to LM628)
let

V = velocity (units = counts/sample)

let

T = sample time (seconds) = 341 ","S (with 6 MHz
clock)

let

C = conversion factor = 1 mlnute/60 seconds

In operation, the filter algorithm receives a 16-bit error signal
from the loop summing-junction. The error signal is saturated at 16 bits to ensure predictable behavior. In addition to
being multiplied by filter coefficient kp, the error signal is
added to an accumulation of previous errors (to form the
integral signal) and, at a rate determined by the chosen derivative sampling interval, the previous error is subtracted
from it (to form the derivative signal). All filter multiplications
are 16-bit operations; only the bottom 16 bits of the product
are used.

then V = R • T • C • desired rpm
and V = 2000' 341E-6 • 1/60 * 600 rpm
V = 6.82 counts/sample

V (scaled) = 6.82 • 65,536 = 446,955.52
V (rounded) = 446,956 (value to load)
V (coding) = 000601 EC (hex code written to LM628)
let

A = acceleration (units = counts/sample/sample)

The integral signal is maintained to 24 bits, but only the top
16 bits are used. This scaling technique results in a more
usable (less sensitive) range of coefficient ki values. The 16
bits are right-shifted eight positions and multiplied by filter
coefficient ki to form the term which contributes to the motor control output. The absolute magnitude of this product is
compared to coefficient ii, and the lesser, appropriately
signed magnitude then contributes to the motor control signal.
The derivative signal is multiplied by coefficient kd each derivative sampling interval. This product contributes to the
motor control output every sample interval, independent of
the user-chosen derivative sampling interval.

A = R • T • T • desired acceleration (rev/sec/sec)
then A = 2000 • 341E-6 • 341E-6 • 1 rev/sec/sec
and A = 2.33E-4 counts/sample/sample
A (scaled) = 2.33E-4 • 65,536 = 15.24
A (rounded) = 15 (value to load)

A (coding) = OOOOOOOF (hex code written to LM628)
The above position, velocity, and acceleration values must
be converted to binary codes to be loaded into the LM628.
The values shown for velocity and acceleration must be
multiplied by 65,536 (as shown) to adjust for the required
integer/fraction format of the input data. Note that after
scaling the velocity and acceleration values, literal fractional
data cannot be loaded; the data must be rounded and converted to binary. The factor of four increase in system resolution is due to the method used to decode the quadrature
encoder signals, see Figure 9.

The kp, limited ki, and kd product terms are summed to form
a 16-bit quantity. Depending on the output mode (wordsize),
either the top 8 or top 12 bits become the motor control
output signal.

PID COMPENSATION FILTER

LM628 READING AND WRITING OPERATIONS

The LM628 uses a digital Proportional Integral Derivative
(PID) filter to compensate the control loop. The motor is
held at the desired position by applying a restoring force to
the motor that is proportional to the position error, plus the
integral of the error, plus the derivative of the error. The
following discrete-time equation illustrates the control performed by the LM628:
n

The host processor writes commands to the LM628 via the
host I/O port when Port Select (ps) input (Pin 16) is logic
low. The desired command code is applied to the parallel
port line and the Write (WR) input (Pin 15) is strobed. The
command byte is latched into the LM628 on the rising edge
of the WR input. When writing command bytes it is necessary to first read the status byte and check the state of a
flag called the "busy bit" (Bit 0). If the busy bit is logic high,
no command write may take place. The busy bit is never
high longer than 100 ","S, and typically falls within 15 ","S to
25 ","s.

u(n) = kp*e(n)

+ kiL

e(n)

+

N=O
kd[e(n') - e(n' - 1)1

The host processor reads the LM628 status byte in a similar
manner: by strobing the Read (RD) input (Pin 13) when PS
(Pin 16) is low; status information remains valid as long as
RD is low.

(Eq.1)

where u(n) is the motor control signal output at sample time
n, e(n) is the position error at sample time n, n' indicates sampling at the derivative sampling rate, and
kp, ki, and kd are the discrete-time filter parameters
loaded by the users.

Writing and reading data to/from the LM628 (as opposed to
writing commands and reading status) are done with PS (Pin
16) logic high. These writes and reads are always an integral number (from one to seven) of two-byte words, with the
first byte of each word being the more significant. Each byte
requires a write (WR) or read (RD) strobe. When transferring
data words (byte-pairs), it is necessary to first read the
status byte and check the state of the busy bit. When the

The first term, the proportional term, provides a restoring
force porportional to the position error, just as does a spring
obeying Hooke's law. The second term, the integration
term, provides a restoring force that grows with time, and
thus ensures that the static position error is zero. If there is
4-36

r-----------------------------------------------------------------------------~

r

3:
0)

Theory of Operation (Continued)
busy bit is logic low, the user may then sequentially transfer
both bytes comprising a data word, but the busy bit must
again be checked and found to be low before attempting to
transfer the next byte pair (when transferring multiple
words). Data transfers are accomplished via LM628-internal
interrupts (which are not nested); the busy bit informs the
host processor when the LM628 may not be interrupted for
data transfer (or a command byte). If a command is written
when the busy bit is high, the command will be ignored.

The LM629 provides 8-bit, sign and magnitude PWM output
signals for directly driving switch-mode motor-drive amplifiers. Figure 11 shows the format of the PWM magnitude output signal.

~
r

3:

0)

N
CD

PWM MAGNITUDE WAVEfORMS (pin 19):

DUTY CYCLE:

o

1 (ON)

(a) 128= Off 0 _ _ _ _ _ _ _ _ _ _ __

_L- MIN
(b) 128-DRIVE

The busy bit goes high immediately after writing a command
byte, or reading or writing a second byte of data (See Figures 5 thru 7).

~D~
r-~
1 r- ic~
256

'1 I" 'elK

(c)M=50~ l r L J L J L J L . r

MOTOR OUTPUTS

128 DRIVE

The LM628 DAC output port can be configured to provide
either a latched eight-bit parallel output or a multiplexed
12-bit output. The 8-bit output can be directly connected to
a flow-through (non-input-Iatching) DfA converter; the 12-bit
output can be easily demultiplexed using an external 6-bit
latch and an input-latching 12-bit Df A converter. The DAC
output data is offset-binary coded; the 8-bit code for zero is
80 hex and the 12-bit code for zero is 800 hex. Values less
than these cause a negative torque to be applied to the
motor and, conversely, larger values cause positive motor
torque. The LM628, when configured for 12-bit output, provides signals which control the demultiplexing process. See
Figure 8 for details.

D
508

MAX

(d)

g~=POS

"1 I"
r-IfII1rIr
'CLK

1

DRIVE 0

I - - 2048

,

1CLK

I

128 MAX 1 - - - . . . . ; ; ; ; ; ; . . - - - - - - (e) 128 = NEG 0 (Off)
DRIVE
TL/H/9219-13

Note: Sign output (pin 18) not shown

FIGURE 11. PWM Output Signal Format

TABLE II. LM628 User Command Set
Command
RESET
PORT8
PORT12
DFH
SIP
LPEI
LPES
SBPA
SBPR
MSKI
RSTI
LFIL
UDF
LTRJ
STT
RDSTAT
RDSIGS
RDIP
RDDP
RDRP
RDDV
RDRV
RDSUM

Type

Description

Hex

Initialize
Initialize
Initialize
Initialize
Interrupt
Interrupt
Interrupt
Interrupt
Interrupt
Interrupt
Interrupt
Filter
Filter
Trajectory
Trajectory
Report
Report
Report
Report
Report
Report
Report
Report

ResetLM628
Select 8-Bit Output
Select 12-Bit Output
Define Home
Set Index Position
Interrupt on Error
Stop on Error
Set Breakpoint, Absolute
Set Breakpoint, Relative
Mask Interrupts
Reset Interrupts
Load Filter Parameters
Update Filter
Load Trajectory
Start Motion
Read Status Byte
Read Signals Register
Read Index Position
Read Desired Position
Read Real Position
Read Desired Velocity
Read Real Velocity
Read Integration Sum

00
05
06
02
03
1B
1A
20
21
1C

10
1E
04
1F
01
None
OC
09
08
OA
07
OB
OD

Note 1: Commands may be executed "On the Fly" during motion.

Note 2: Commands not applicable to execution during motion.
Note 3: Command may be executed during motion If acceleration parameter was not changed.
Nota 4: Command needs no code because the command port status-byte read is totally supported by hardware.

4-37

Data
Bytes

Note

0
0
0
0
0
2
2
4
4
2
2
2to 10
0
2to 14
0
1
2
4
4
4
4
2
2

1
2
2
1
1
1
1
1
1
1
1
1
1
1
3
1,4
1
1
1
1
1
1
1

•

mediately executed. This command must not be issued
when using an 8-bit converter or the LM629, the PWM-output version of the LM628.

User Command Set
GENERAL
The following paragraphs describe the user command set of
the LM628. Some of the commands can be issued alone
and some require a supporting data structure. As examples,
the command STT (STarT motion) does not require additional data; command LFIL (Load Filter parameters) requires additional data (derivative-term sampling interval
and! or filter parameters).

DFH COMMAND: DeFine Home
Command Code:
02 Hex
Data Bytes:
None
Executable During Motion: Yes
This command declares the current position as "home", or
absolute position 0 (Zero). If DFH is executed during motion
it will not affect the stopping position of the on-going move
unless command STT is also executed.

Commands are categorized by function: initialization, interrupt control, filter control, trajectory control, and data reporting. The commands are listed in Table II and described in
the following paragraphs. Along with each command name
is its command-byte code, the number of accompanying
data bytes that are to be written (or read), and a comment
as to whether the command is executable during motion.

Interrupt Control Commands
The following seven LM628 user commands are associated
with conditions which can be used to interrupt the host computer. In order for any of the potential interrupt conditions to
actually interrupt the host via Pin 17, the corresponding bit
in the interrupt mask data associated with command MSKI
must have been set to logic high (the non-masked state).
The identity of all interrupts is made known to the host via
reading and parsing the status byte. Even if all interrupts are
masked off via command MSKI, the state of each condition
is still reflected in the status byte. This feature facilitates
polling the LM628 for status information, as opposed to interrupt driven operation.

Initialization Commands
The following four LM628 user commands are used primarily to initialize the system for use.
RESET COMMAND: RESET the LM628
00 Hex
Command Code:
Data Bytes:
None
Executable During Motion: Yes
This command (and the hardware reset input, Pin 27) results in setting the following data items to zero: filter coefficients and their input buffers, trajectory parameters and
their input buffers, and the motor control output. A zero motor control output is a half-scale, offset-binary code: (80 hex
for the 8-bit output mode; 800 hex for 12-bit mode). During
reset, the DAC port outputs 800 hex to "zero" a 12-bit DAC
and reverts to 80 hex to "zero" an 8-bit DAC. The command
also clears five of the six interrupt masks (only the SBPAI
SBPR interrupt is masked), sets the output port size to
8 bits, and defines the current absolute position as home.
Reset, which may be executed at any time, will be completed in less than 1.5 ms. Also see commands PORT8 and
PORT12.

SIP COMMAND: Set Index Position
Command Code:
03 Hex
Data Bytes:
None
Executable During Motion: Yes
After this command is executed, the absolute position which
corresponds to the occurrence of the next index pulse input
will be recorded in the index register, and bit 3 of the status
byte will be set to logiC high. The position Is recorded when
both encoder-phase inputs and the index pulse input are
logic low. This register can then be read by the user (see
description for command RDIP) to facilitate aligning the definition of home pOSition (see description of command DFH)
with an index pulse. The user can also arrange to have the
LM628 interrupt the host to signify that an index pulse has
occurred. See the descriptions for commands MSKI and
RSTI.

PORT8 COMMAND: Set Output PORT Size to 8 Bits
Command Code:
05 Hex
Data Bytes:
None
Executable During Motion: Not Applicable

LPEI COMMAND: Load Position Error for Interrupt
Command Code:
1B Hex
Data Bytes:
Two
Data Range:
0000 to 7FFF Hex
Executable During Motion: Yes

The default output port size of the LM628 is 8 bits; so the
PORT8 command need not be executed when using an
8-blt DAC. This command must not be executed when using
a 12-bit converter; it will result in erratic, unpredictable motor behavior. The 8-bit output port size is the required selection when using the LM629, the PWM-output version of the
LM628.

An excessive position error (the output of the loop summing
junction) can indicate a serious system problem; e.g., a
stalled rotor. Instruction LPEI allows the user to input a
threshold for position error detection. Error detection occurs
when the absolute magnitude of the pOSition error exceeds
the threshold, which results In bit 5 of the status byte being
set to logiC high. If it is desired to also stop (turn off) the
motor upon detecting excessive position error, see command LPES, below. The first byte of threshold data written
with command LPEI is the more significant. The user can
have the LM628 interrupt the host to signify that an excessive position error has occurred. See the descriptions for
commands MSKI and RSTI.

PORT12 COMMAND: Set Output PORT Size to 12 Bits
Command Code:
06 Hex
Data Bytes:
None
Executable During Motion: Not Applicable
When a 12-bit DAC is used, command PORT12 should be
issued very early in the initialization process. Because use
of this command is determined by system hardware, there is
only one foreseen reason to execute it later: if the RESET
command is issued (because an 8-bit output would then be
selected as the default) command PORT12 should be im-

4-38

Interrupt Control Commands (Continued)
LPES COMMAND: Load Position Error for Stopping
Command Code:
1A Hex
Data Bytes:
Two
Data Range:
0000 to 7FFF Hex
Executable During Motion: Yes
Instruction LPES is essentially the same as command LPEI
above, but adds the feature of turning off the motor upon
detecting excessive position error. The motor drive is not
actually switched off, it Is set to half-scale, the offset-binary
code for zero. As with command LPEI, bit 5 of the status
byte is also set to logic high. The first byte of threshold data
written with command LPES is the more significant. The
user can have the LM628 interrupt the host to signify that an
excessive position error has occurred. See the descriptions
for commands MSKI and RSTI.

6-bit field will mask the corresponding interrupt(s); any
one(s) enable the interrupt(s). Other bits comprising the two
bytes have no effect. The mask controls only the host interrupt process; reading the status byte will still reflect the actual conditions independent of the mask byte. See Table III.
TABLE III. Mask and Reset Bit Allocations for Interrupts

SBPA COMMAND:
Command Code:
Data Bytes:
Data Range:
Executable During Motion:

20 Hex
Four
COOOOOOO to 3FFFFFFF Hex
Yes

Function
Not Used
Breakpoint Interrupt
Position-Error Interrupt
Wrap-Around Interrupt
Index-Pulse Interrupt
Trajectory-Complete Interrupt
Command-Error Interrupt
Not Used

RSTI COMMAND: ReSeT Interrupts
Command Code:
Data Bytes:
Data Range:
Executable During Motion:

This command enables the user to set a breakpoint in terms
of absolute position. Bit 6 of the status byte is set to logic
high when the breakpoint position is reached. This condition
is useful for signaling trajectory and/or filter parameter updates. The user can also arrange to have the LM628 interrupt the host to signify that a breakpoint position has been
reached. See the descriptions for commands MSKI and
RSTI.

10 Hex
Two
See Text
Yes

When one of the potential interrupt conditions of Table III
occurs, command RSTI is used to reset the corresponding
interrupt flag bit in the status byte. The host may reset one
or all flag bits. Resetting them one at a time allows the host
to service them one at a time according to a priority programmed by the user. As in the MSKI command, bits 1
through 6 of the second (less significant) byte correspond to
the potential Interrupt conditions shown in Table III. Also
see description of RDSTAT command. Any zero(s) in this
6-bit field reset the corresponding Interrupt(s). The remaining bits have no effect.

SBPR COMMAND:
Command Code:
21 Hex
Data Bytes:
Four
Data Range:
See Text
Executable During Motion: Yes
This command enables the user to set a breakpoint in terms
of relative position. As with command SBPA, bit 6 of the
status byte is set to logic high when the breakpoint position
(relative to the current commanded target position) is
reached. The relative breakpoint input value must be such
that when this value is added to the target position the result
remains within the absolute position range of the system
(COOOOOOO to 3FFFFFFF hex). This condition is useful for
signaling trajectory and/or filter parameter updates. The
user can also arrange to have the LM628 interrupt the host
to signify that a breakpoint position has been reached. See
the descriptions for commands MSKI and RSTI.

Filter Control Commands
The following two LM628 user commands are used for setting the derivative-term sampling interval, for adjusting the
filter parameters as required to tune the system, and to control the timing of these system changes.
LFIL COMMAND: Load Filter Parameters
Command Code:
1E Hex
Data Bytes:
Two to Ten
Data Ranges ...
See Text
Filter Control Word:
Filter Coefficients:
0000 to 7FFF Hex (Pos Only)
Integration Limit:
0000 to 7FFF Hex (Pos Only)
Executable During Motion: Yes
The filter parameters (coefficients) which are written to the
LM628 to control loop compensation are: kp, ki, kd, and iI
(integration limit). The integration limit (iI) constrains the
contribution of the integration term

MSKI COMMAND: MaSK Interrupts
Command Code:
Data Bytes:
Data Range:
Executable During Motion:

Bit Position
Bits 15 thru 7
Bit 6
Bit 5
Bit4
Bit3
Bit2
Bit 1
Bit 0

1C Hex
Two
See Text
Yes

The MSKI command lets the user determine which potential
interrupt condition(s) will interrupt the host. Bits 1 through 6
of the status byte are indicators of the six conditions which
are candidates for host interrupt(s). When interrupted, the
host then reads the status byte to learn which condition(s)
occurred. Note that the MSKI command is immediately followed by two data bytes. Bits 1 through 6 of the second
(less significant) byte written determine the masked/unmasked status of each potential interrupt. Any zero(s) in this

[ki

·to

e(n)]

(see Eq. 1) to values equal to or less than a user-defined
maximum value; this capability minimizes integral or reset
"wind-up" (an overshooting effect of the integral action).
The positive-only input value is compared to the absolute

4-39

en

('II

CD

:i

;0
('II

CD

:i

r-------------------------------------------------------------------------------~

Filter Control Commands (Continued)
magnitude of the integration term; when the magnitude of
integration term value exceeds ii, the iI value (with appropriate sign) is substituted for the integration term value.
The derivative-term sampling interval is also programmable
via this command. After writing the command code, the first
two data bytes that are written specify the derivative-term
sampling interval and which of the four filter parameters
is/are to be written via any forthcoming data bytes. The first
byte written is the more significant. Thus the two data bytes
constitute a filter control word that informs the LM628 as to
the nature and number of any following data bytes. See
Table IV.

The data bytes specified by and immediately following the
filter control word are written in pairs to comprise 16-bit
words. The order of sending the data words to the LM628
corresponds to the descending order shown in the above
description of the filter control word; i.e., beginning with kp,
then ki, kd and iI. The first byte of each word is the more-significant byte. Prior to writing a word (byte pair) it is necessary to check the busy bit in the status byte for readiness.
The required data is written to the primary buffers of a double-buffered scheme by the above described operations; it
is not transferred to the secondary (working) registers until
the UDF command is executed. This fact can be used advantageously; the user can input numerous data ahead of
their actual use. This simple pipeline effect can relieve potential host computer data communications bottlenecks,
and facilitates easier synchronization of multiple-axis controls.
UDF COMMAND: UpDate Filter

TABLE IV. Filter Control word Bit Allocation
Bit Position

Function

Bit 15
Bit 14
Bit 13
Bit 12
Bit 11
Bit 10
Bit 9
Bit 8
Bit 7
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
Bit 0

Derivative Sampling Interval Bit 7
Derivative Sampling Interval Bit 6
Derivative Sampling Interval Bit 5
Derivative Sampling Interval Bit 4
Derivative Sampling Interval Bit 3
Derivative Sampling Interval Bit 2
Derivative Sampling Interval Bit 1
Derivative Sampling Interval Bit 0
Not Used
Not Used
Not Used
Not Used
Loading kp Data
Loading ki Data
Loading kd Data
Loading iI Data

04 Hex
Command Code:
Data Bytes:
None
Executable During Motion: Yes
The UDF command is used to update the filter parameters,
the specifics of which have been programmed via the LFIL
command. Any or all parameters (derivative-term sampling
interval, kp, ki, kd, and/or il) may be changed by the appropriate command(s), but command UDF must be executed to
affect the change in filter tuning. Filter updating is synchronized with the calculations to eliminate erratic or spurious
behavior.

Trajectory Control Commands
The following two LM628 user commands are used for
setting the trajectory control parameters (pOSition, velocity,
acceleration), mode of operation (position or velocity), and
direction (velocity mode only) as required to describe a desired motion or to select the mode of a manually directed
stop, and to control the timing of these system changes.

Bits 8 through 15 select the derivative-term sampling interval. See Table V. The user must locally save and restore
these bits during successive writes of the filter control word.
Bits 4 through 7 of the filter control word are not used.
Bits 0 to 3 inform the LM628 as to whether any or all of the
filter parameters are about to be written. The user may
choose to update any or all (or none) of the filter parameters. Those chosen for updating are so indicated by logic
one(s) in the corresponding bit position(s) of the filter control word.

LTRJ COMMAND: Load TRaJectory Parameters
Command Code:
1F Hex
Data Bytes:
Two to Fourteen
Data Ranges ... '
Trajectory Control Word: See Text
Position:
COOOOOOO to 3FFFFFFF Hex
00000000 to 3FFFFFFF Hex
Velocity:
(Pos Only)
Acceleration:
00000000 to 3FFFFFFF Hex
(Pos Only)
Executable During Motion: Conditionally, See Text

TABLE V. Derivative-Term Sampling Interval Selection Codes
Bit Position

thru

15

14

13

12

11

10

9

8

0
0
0
0

0
0
0
0

0
0
0
0

0
0
0
0

0
0
0
0

0
0
0
0

0
0
1
1

0
1
0
1

1

1

1

1

1

1

1

1

Selected Derivative
Sampling Interval
256 fLS
512/1-s
768/1-s
1024/1-s, etc ...
65,536/1-s

Note: Sampling Intervals shown are when using an 8.0 MHz clock. The 256 corresponds to 2048/8 MHz; sample intervals must be scaled for other clock

frequencies.

4-40

Trajectory Control Commands (Continued)
The trajectory control parameters which are written to the
LM628 to control motion are: acceleration, velocity, and position. In addition, indications as to whether these three parameters are to be considered as absolute or relative inputs,
selection of velocity mode and direction, and manual stopping mode selection and execution are programmable via
this command. After writing the command code, the first two
data bytes that are written specify which parameter(s) isl are
being changed. The first byte written is the more significant.
Thus the two data bytes constitute a trajectory control word
that informs the LM628 as to the nature and number of any
following data bytes. See Table VI.

none) of the trajectory parameters. Those chosen for updating are so indicated by logic one(s) in the corresponding bit
position(s). Any parameter may be changed while the motor
is in motion; however, if acceleration is changed then the
next STT command must not be issued until the LM628 has
completed the current move or has been manually stopped.
The data bytes specified by and immediately following the
trajectory control word are written in pairs which comprise
16-bit words. Each data item (parameter) requires two 16-bit
words; the word and byte order is most-to-Ieast significant.
The order of sending the parameters to the LM628 corresponds to the descending order shown in the above description of the trajectory control word; i.e., beginning with
acceleration, then velocity, and finally position.
Acceleration and velocity are 32 bits, positive only, but
range only from 0 (00000000 hex) to [230]-1 (3FFFFFFF
hex). The bottom 16 bits of both acceleration and velocity
are scaled as fractional data; therefore, the least-significant
integer data bit for these parameters is bit 16 (where the bits
are numbered 0 through 31). To determine the coding for a
given velocity, for example, one multiplies the desired velocity (in counts per sample interval) times 65,536 and converts
the result to binary. The units of acceleration are counts per
sample per sample. The value loaded for acceleration must
not exceed the value loaded for velocity. Position is a
signed, 32-bit integer, but ranges only from - [230]
(COOOOOOO hex) to [230]-1 (3FFFFFFF Hex).

TABLE VI. Trajectory Control Word Bit Allocation
Bit Position
Bit15

Function
Not Used

Bit14

Not Used

Bit 13

Not Used

Bit12

Forward Direction (Velocity Mode Only)

Bit11

Velocity Mode

Bit10

Stop Smoothly (Decelerate as Programmed)

Bit 9

Stop Abruptly (Maximum Deceleration)

Bit 8

Tum Off Motor (Output Zero Drive)

Bit 7

Not Used

Bit 6

Not Used

Bit 5

Acceleration Will Be Loaded

B~

Acceleration Data Is Relative

4

Bit 3

Velocity Will Be Loaded

B~

Velocity Data Is Relative

2

Bit 1

Position Will Be Loaded

Bit 0

Position Data Is Relative

The required data is written to the primary buffers of a double-buffered scheme by the above described operations; it
is not transferred to the secondary (working) registers until
the STT command is executed. This fact can be used advantageously; the user can input numerous data ahead of
their actual use. This simple pipeline effect can relieve potential host computer data communications bottlenecks,
and facilitates easier synchronization of multiple-axis controls.

Bit 12 determines the motor direction when in the velocity
mode. A logic one indicates forward direction. This bit has
no effect when in position mode.
Bit 11 determines whether the LM628 operates in velocity
mode (Bit 11 logic one) or position mode (Bit 11 logic zero).
Bits 8 through 10 are used to select the method of manually
stopping the motor. These bits are not provided for one to
merely specify the desired mode of stopping, in position
mode operations, normal stopping is always smooth and
occurs automatically at the end of the specified trajectory.
Under exceptional circumstances it may be desired to manually intervene with the trajectory generation process to affect a premature stop. In velocity mode operations, however, the normal means of stopping is via bits 8 through 10
(usually bit 10). Bit 8 is set to logic one to stop the motor by
turning off motor drive output (outputting the appropriate offset-binary code to apply zero drive to the motor); bit 9 is set
to one to stop the motor abruptly (at maximum available
acceleration, by setting the target position equal to the current position); and bit 10 is set to one to stop the motor
smoothly by using the current user-programmed acceleration value. Bits 8 through 10 are to be used exclusively; only
one bit should be a logiC one at any time.
Bits 0 through 5 inform the LM628 as to whether any or all
of the trajectory contrOlling parameters are about to be written, and whether the data should be interpreted as absolute
or relative. The user may choose to update any or all (or

STT COMMAND: STarT Motion Control
Command Code:
01 Hex
Data Bytes:
None
Executable During Motion: Yes, if acceleration has not
been changed
The STT command is used to execute the desired trajectory, the specifics of which have been programmed via the
LTRJ command. Synchronization of multi-axis control (to
within one sample interval) can be arranged by loading the
required trajectory parameters for each (and every) axis and
then simultaneously issuing a Single STT command to all
axes. This command may be executed at any time, unless
the acceleration value has been changed and a trajectory
has not been completed or the motor has not been manually stopped. If STT is issued during motion and acceleration
has been changed, a command error interrupt will be generated and the command will be ignored.

Data Reporting Commands
The following seven LM628 user commands are used to
obtain data from various registers in the LM628. Status, position, and velocity information are reported. With the exception of RDSTAT, the data is read from the LM628 data port
after first writing the corresponding command to the command port.

4-41

Data Reporting Commands (Continued)
Bit 2, the trajectory complete interrupt flag, is set to logic
one when the trajectory programmed by the LTRJ comcommand has been completmand and initiated by the
ed. Because of overshoot or a limiting condition (such as
commanding the velocity to be higher than the motor can
achieve), the motor may not yet be at the final commanded
pOSition. This bit is the logical OR of bits 7 and 10 of the
Signals Register, see command RDSIGS below. The flag
functions independently of the host interrupt mask status.
Bit 21s cleared via command RSTI.
Bit 1, the command-error interrupt flag, Is set to logic one
when the user attempts to read data when a write was appropriate (or vice versa). The flag Is functional independent
of the host Interrupt mask status. Bit 1 Is cleared via command RSTI.
Bit 0, the busy flag, is frequently tested by the user (via the
host computer program) to determine the busy/ready status
prior to writing and reading any data. Such writes and reads
may be executed only when bit 0 Is logic zero (not busy).
Any command or data writes when the busy bit is high will
be ignored. Any data reads when the busy bit Is high will
read the current contents of the I/O port buffers, not the
data expected by the host. Such reads or writes (with the
busy bit high) will not generate a command-error Interrupt.
RDSIGS COMMAND: ReaD SIGnalS Register
OC Hex
Command Code:
Bytes Read:
Two
Data Range:
See Text
Executable During Motion: Yes

RDSTAT COMMAND: ReaD STATus Byte
Command Code:
None
Byte Read:
One
Data Range:
See Text
Executable During Motion: Yes
The RDSTAT command is really not a command, but is listed with the other commands because it is used very frequently to control communications with the host computer.
There is no Identification code; it is directly supported by the
hardware and may be executed at any time. The single-byte
status read is selected by placing CS, ~ and 'AD at logic
zero. See Table VII.

sn

TABLE VII. Status Byte Bit Allocation
Bit Position

Function

Bit 7
Blt6
Bit 5
Bit4
Bit 3
Bit2
Bit 1
BltO

Motor Off
Breakpoint Reached [Interrupt]
Excessive Position Error [Interrupt]
Wraparound Occurred [Interrupt]
Index Pulse Observed [Interrupt]
Trajectory Complete [Interrupt]
Command Error [Interrupt]
Busy Bit

Bit 7, the motor-off flag, is set to logic one when the motor
drive output Is off (at the half-scale, offset-binary code for
zero). The motor Is turned off by any of the following conditions: power-up reset, command RESET, excessive position
error (If command LPES had been executed), or when command LTRJ is used to manually stop the motor via turning
the motor off. Note that when bit 7 is set In conjunction with
command LTRJ for producing a manual, motor-off stop, the
actual setting of bit 7 does not occur until command
is
issued to affect the stop. Bit 7 is cleared by command
except as described in the previous sentence.

The LM628 internal "signals" register may be read using
this command. The first byte read Is the more significant.
The less significant byte of this register (with the exception
of bit 0) duplicates the status byte. See Table VIII.

sn
sn,

TABLE VIII. Signals Register Bit Allocation

Bit 6, the breakpoint-reached interrupt flag, is set to logic
one when the position breakpoint loaded via command
SBPA or SBPR has been exceeded. The flag is functional
independent of the host interrupt mask status. Bit 6 is
cleared via command RSTi.
Bit 5, the excessive-position-error interrupt flag, is set to
logic one when a position-error interrupt condition exists.
This occurs when the error threshold loaded via command
LPEI or LPES has been exceeded. The flag is functional
independent of the host interrupt mask ·status. Bit 5 is
cleared via command RSTI.
. .
Bit 4, the wraparound interrupt flag, is set to logic one when
a numerical "wraparound" has occurred. To "wraparound"
means to exceed the position address space of the LM628,
which could occur during velocity mode operation. If a wraparound has occurred, then position information will be in
error and this interrupt helps the user to ensure position
data integrity. The flag is functional independent of the host
interrupt mask status. Bit 4 is cleared via command RSTi.
Bit 3, the index-pulse acquired interrupt flag, is set to logic
one when an index pulse has occurred (if command SIP had
been executed) and indicates that the index position register has been updated. The flag is functional independent of
the host interrupt mask status. Bit 3 is cleared by command
RSTi.

Bit Position

Function

Bit 15
Bit 14
Bit 13
Bit 12
Bit 11
Bit 10
Bit 9
Bit 8
Bit 7
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
Bit 0

Host Interrupt
Acceleration Loaded (But Not Updated)
UDF Executed (But Filter Not yet Updated)
Forward Direction
Velocity Mode
On Target
Turn Off upon Excessive Position Error
Eight-Bit Output Mode
Motor Off
Breakpoint Reached [Interrupt]
Excessive Position Error [Interrupt]
Wraparound Occurred [Interrupt]
Index Pulse Acquired [Interrupt]
Trajectory Complete [Interrupt]
Command Error [Interrupt]
Acquire Next Index (SIP Executed)

Bit 15, the host interrupt flag, is set to logic one when the
host interrupt output (Pin 17) is logic one. Pin· 17 is set to
logiC one when any of the six host interrupt conditions occur
(if the corresponding interrupt has not been masked). Bit 15
(and Pin 17) are cleared via command RSTi.
Bit 14, the acceleration-loaded flag, is set to logic one when
acceleration data is written to the LM628. Bit 14 is cleared
by the
command.

sn

4-42

rs::
en

Data Reporting Commands (Continued)

N

This command reads the current actual position of the motor. This is the feedback input to the loop summing junction.
The bytes are read in most-to-Ieast significant order.

Bit 13, the UDF-executed flag, is set to logic one when the
UDF command is executed. Because bit 13 is cleared at the
end of the sampling interval in which it has been set, this
signal is very short-lived and probably not very profitable for
monitoring.
Bit 12, the forward direction flag, is meaningful only when
the LM628 is in velocity mode. The bit is set to logic one to
indicate that the desired direction of motion is "forward";
zero indicates "reverse" direction. Bit 12 is set and cleared
via command LTRJ. The actual setting and clearing of bit 12
does not occur until command STT is executed.

RDDV COMMAND: ReaD Desired Velocity
Command Code:
Bytes Read:
Data Range:
Executable During Motion:

This command reads the integer and fractional portions of
the instantaneous desired (current temporal) velocity, as
used to generate the desired position profile. The bytes are
read in most-to-Ieast significant order. The value read is
properly scaled for numerical comparison with the user-supplied (commanded) velocity; however, because the two
least-significant bytes represent fractional velocity, only the
two most-significant bytes are appropriate for comparison
with the data obtained via command RDRV (see below).
Also note that, although the velocity input data is constrained to positive numbers (see command LTRJ), the data
returned by command RDDV represents a signed quantity
where negative numbers represent operation in the reverse
direction.

Bit 11, the velocity mode flag, is set to logic one to indicate
that the user has selected (via command LTRJ) velocity
mode. Bit 11 is cleared when position mode is selected (via
command LTRJ). The actual setting and clearing of bit 11
does not occur until command STT is executed.
Bit 10, the on-target flag, is set to logic one when the trajectory generator has completed its functions for the last-issued STT command. Bit 10 is cleared by the next STT command.
Bit 9, the turn-off on-error flag, is set to logic one when
command LPES is executed. Bit 9 is cleared by command
LPEI.

RDRV COMMAND: ReaD Real Velocity

Bit 8, the 8-bit output flag, is set to logic one when the
LM628 is reset, or when command PORT8 is .executed. Bit
8 is cleared by command PORT12.

Command Code:
Bytes Read:
Data Range:
Executable During Motion:

Bits 0 through 7 replicate the status byte (see Table VII),
with the exception of bit o. Bit 0, the acquire next index flag,
is set to logic one when command SIP is executed; it then
remains set until the next index pulse occurs.
09 Hex
Four
COOOOOOO to 3FFFFFFF Hex
Yes

This command reads the position recorded in the index register. Reading the index register can be part of a system
error checking scheme. Whenever the SIP command is executed, the new index position minus the old index position,
divided by the incremental encoder resolution (encoder
lines times four), should always be an integral number. The
RDIP command facilitates acquiring these data for hostbased calculations. The command can also be used to identify/verify home or some other special position. The bytes
are read in most-to-Ieast significant order.

RDSUM COMMAND: ReaD Integration-Term SUMmation
Value
Command Code:
Bytes Read:
Data Range:

OD Hex
Two
00000 Hex to ± the Current
Value of the Integration Limit
Executable During Motion: Yes

This command reads the value to which the integration term
has accumulated. The ability to read this value may be helpful in initially or adaptively tuning the system.

RDDP COMMAND: ReaD Desired Position
Command Code:
Bytes Read:
Data Range:
Executable During Motion:

08 Hex
Four
COOOOOOO to 3FFFFFFF Hex
Yes

Typical Applications
Programming LM628 Host Handshaking (Interrupts)

This command reads the instantaneous desired (current
temporal) position output of the profile generator. This is the
"setpoint" input to the position-loop summing junction. The
bytes are read in most-to-Ieast significant order.

A few words regarding the LM628 host handshaking will be
helpful to the system programmer. As indicated in various
portions of the above text, the LM628 handshakes with the
host computer in two ways: via the host interrupt output (Pin
17), or via polling the status byte for "interrupt" conditions.
When the hardwired interrupt is used, the status byte is also
read and parsed to determine which of six possible conditions caused the interrupt.

RDRP COMMAND: ReaD Real Position
Command Code:
Bytes Read:
Data Range:
Executable During Motion:

OB Hex
Two
COOO to 3FFF Hex, See Text
Yes

This command reads the integer portion of the instantaneous actual velocity of the motor. The internally maintained
fractional portion of velocity is not reported because the
reported data is derived by reading the incremental encoder, which produces only integer data. For comparison with
the result obtained by executing command RDDV (or the
user-supplied input value), the value returned by command
RDRV must be multiplied by 216 (shifted left 16 bit positions). Also, as with command RDDV above, data returned
by command RDRV is a signed quantity, with negative values representing reverse-direction motion.

RDIP COMMAND: ReaD Index Position
Command Code:
Bytes Read:
Data Range:
Executable During Motion:

07 Hex
Four
C0000001 to 3FFFFFFF
Yes

OA Hex
Four
COOOOOOO to 3FFFFFFF Hex
Yes

4-43

co

"rs::
en
N

CD

en

N
CD

:::iii

..J

re
CD

:::iii

..J

r------------------------------------------------------------------------------------------,
Typical Applications (Continued)
When using the hardwired interrupt it is very important that
the host interrupt service routine does not interfere with a
command sequence which might have been in progress
when the interrupt occurred. If the host interrupt service routine were to issue a command to the LM628 while it is in the
middle of an ongoing command sequence, the ongoing
command will be aborted (which could be detrimental to the
application).
Two approaches exist for avoiding this problem. If one is
using hardwired interrupts, they should be disabled at the
host prior to issuing any LM628 command sequence, and
re-enabled after each command sequence. The second approach is to avoid hardwired interrupts and poll the LM628
status byte for "interrupt" status. The status byte always
reflects the interrupt-condition status, independent of
whether or not the interrupts have been masked.

A Monolithic Linear Drive Using LM12 Power Op Amp
Figure 15 shows a motor-drive amplifier built using the LM12
Power Operational Amplifier. This circuit is very simple and
can deliver up to 8A at 30V (using the LMI2L/LMI2CL).
Resistors Rl and R2 should be chosen to set the gain to
provide maximum output voltage consistent with maximum
input voltage. This example provides a gain of 2.2, which
allows for amplifier output saturation at ± 22V with a ± 10V
input, assuming power supply voltages of ±30V. The amplifier gain should not be higher than necessary because the
system is non-linear when saturated, and because gain
should be controlled by the LM628. The LM12 can also be
configured as a current driver, see 1987 Linear Databook,
Vol. 1, p. 2-280.

Typical PWM Motor Drive Interfaces
Figure 16 shows an LM18298 dual full-bridge driver interfaced to the LM629 PWM outputs to provide a switch-mode
power amplifier for driving small brush/commutator motors.
Figure 17 shows an LM621 brushless motor commutator
interfaced to the LM629 PWM outputs and a discrete device
switch-mode power amplifier for driving brushless DC motors.

Typical Host Computer/Processor Interface
The LM628 is interfaced with the host computer/processor
via an 8-bit parallel bus. Figure 12 shows such an interface
and a minimum system configuration.
As shown in Figure 12, the LM628 interfaces with the host
data, address and control lines. The address lines are decoded to generate the LM628 CS input; the host address
LSB directly drives the LM628 PS input. Figure 12 also
shows an 8-bit DAC and an LM12 Power Op Amp interfaced
to the LM628.

Incremental Encoder Interface
The incremental (position feedback) encoder interface consists of three lines: Phase A (Pin 2); Phase B (Pin 3), and
Index (Pin 1). The index pulse output is not available on
some encoders. The LM628 will work with both encoder
types, but commands SIP and RDIP will not be meaningful
without an index pulse (or alternative input for this input ...
be sure to tie Pin 1 high if not used).
Some consideration is merited relative to use in high Gaussian-noise environments. If noise is added to the encoder
inputs (either or both inputs) and is such that it is not sustained until the next encoder transition, the LM628 decoder
logic will reject it. Noise that mimics quadrature counts or
persists through encoder transitions must be eliminated by
appropriate EMI design.
Simple digital "filtering" schemes merely reduce susceptibility to noise (there will always be noise pulses longer than
the filter can eliminate). Further, any noise filtering scheme
reduces decoder bandwidth. In the LM628 it was decided
(since simple filtering does not eliminate the noise problem)
to not include a noise filter in favor of offering maximum
possible decoder bandwidth. Attempting to drive encoder
Signals too long a distance with simple TTL lines can also
be a source of "noise" in the form of Signal degradation
(poor risetime and/or ringing). This can also cause a system
to lose positional integrity. Probably the most effective
countermeasure to noise induction can be had by using balanced-line drivers and receivers on the encoder inputs. Figure 18 shows circuitry using the DS26LS31 and DS26LS32.

LM628 and High Performance Controller (HPC)
Interface
Figure 13 shows the LM628 interfaced to a National HPC
High Performance Controller. The delay and logic associated with the WR line is used to effectively increase the writedata hold time of the HPC (as seen at the LM628) by causing the WR pulse to rise early. Note that the HPC CK2 output provides the clock for the LM628. The 74LS245 is used
to decrease the read-data hold time, which is necessary
when interfacing to fast host busses.

Interfacing a 12-91t DAC
Figure 14 illustrates use of a 12-bit DAC with the LM628.
The 74LS378 hex gated-D flip-flop and an inverter demultiplex the 12-bit output. DAC offset must be adjusted to minimize DAC linearity and monotonicity errors. Two methods
exist for making this adjustment. If the DAC1210 has been
socketed, remove it and temporarily connect a 15 kO resistor between Pins 11 and 13 of the DAC socket (Pins 2 and 6
of the LF356) and adjust the 25 kO potentiometer for OV at
Pin 6 of the LF356.

If the DAC is not removable, the second method of adjustment requires that the DAC121 0 inputs be presented an allzeros code. This can be arranged by commanding the appropriate move via the LM628, but with no feedback from
the system encoder. When the all-zeros code is present,
adjust the pot for OV at Pin 6 of the LF356.

4-44

,-----------------------------------------------------------------------------, r
iii:
en
Typical Applications (Continued)
N

.....
r
CI)

DATA BUS

iii:
en
N
co

8

1+----+-----+100-07
8

Rii

H ~:""'--------+lRii

OACOOAC7

0
S

LM628

T
B
U
S

r----t-;::;t.~T""....:=:::::........:!~~~J

ADDRESS
BUS

r---+....--1---+20V

AO L - - - - - - I M PS

WR

~:.....-------~WR

RESET

~~-------~RST

IRQ

I+~-------~HI

iN A B
2.SK

Note: AV

~ Rl + R2 ::: 2.4

L---+....- ....._---20V

Rl

Rl X R2 ~
k
Rl + R2 - 2.5

• SEE NOTE

ENCODER E

TUH/9219-14

FIGURE 12. Host Interface and Minimum System Configuration

AD-A7
A13
A14
A15
ALE

8

8

00-07

CS

ADDRESS
DECODER
G (eg: HC138)

~

!ill:
RD

RD

WR

WR

CK2

ClK

91

PS
HI

TUH/9219-15

FIGURE 13. LM628 and HPC Interface

4·45

III

LM628/LM629

~
~

»
'a

"2-

OAC

LM628

7

11

6

10

5

9
8 01

4

3

7

2

6

-{>o-

1
0

61-51--

L- 6

8;

~10K

4
3 0

VREF

lfP

CS

~

i'"

A Y500D.

c:

~

9.76K
20K

,yo

4

4~ 3

Q 3 I - - 2 01
2~1

1

1~0

2

IoUTl
lour2

G74LS378
OAC
1210

.--

o

364K

~~

RFB

::::I

OUTPUT
OFFSET

120K

•

20pF

2

+5V

O·

+5.0V

385

5

[

+15V

WRI

~5

.....

Vee

B1/82
XFER

~ WR2

--=-

-

1

-LF356

3 +

6

;"356

5

1 25K

*

~~
IV
IAL
IWER
FIER

+15V

~
~

_....

"'DAe offset must be adjusted to minimize OAe linearity and monotonicity errors. See text.

FIGURE 14. Interfacing a 12-Bit DAC and LM628

TL/H/9219-16

Typical Applications (Continued)
+30V

.I.

+
100}'F

MR752
1.69K

2.0K
R2

MR752

-30V
TL/H/9219-17

FIGURE 15. Driving a Motor with the LM12 Power Op Amp
MOTOR

SUPPLy-------------+-----.----.
VOLTAGE
+5V--------.-.-~

Vss
(PIN 18) SIGN
FROM {
Lt.t629
(PIN 19) MAG

-+----.....

SENSE

A

SENSE

B

TUH/9219-18

FIGURE 16. PWM Drive for Brush/Commutator Motors

II

4·47

Typical Applications (Continued)
r-_ _~_ _.....,f\.IM1T

(X6) r __ .EO!!!! lW.!J£!!~ ___ ,

+

18

+5 VOLTS

I
I

SINK
16

13

(5-40V)
<\>A

#1

lk

MOTOR
SUPPLY
VOLTAGE

I

t-"'I'<'lr-j--t--t
SOURCE

LM621

30/60 SELECT

'------I
lk

24k

BRUSHLESS
MOTOR
COMMUTATOR

SINK

15

I-"'I'<'lr-I+.....--I

12

t-"'I'<.....rt-.::---I

#2

200 pF

SOURCE

DIR

(PIN 18) SIGN

FROM
LII629

1
(PIN

SINK

14 t-Wlr-t+~--t
#3
11

I-W'Ir-++-.::---I
SOURCE

lit;)

ROTOR POSITION
SENSORS

~I)--t++--;

L _ _ _ _ _ _ _ _ _ _ _ _ 01

HSI
HS2
HS3
TL/H/9219-19

FIGURE 17. PWM Drive for Brushless Motors

A

FROt.!
ENCODER

B

TO
LM628

3/4 DS26LS31
TUH/9219-20

FIGURE 18. Typical Balanced-Line Encoder Input Circuit

4-48

lI?A National
~ Semiconductor

LM 18293 Four Channel Push-Pull Driver
General Description
The LM18293 is designed to drive DC loads up to one amp.
Typical applications include driving such inductive loads as
solenoids, relays and stepper motors along with driving
switching power transistors and use as a buffer for low level
logic signals. The four inputs accept standard TTL and DTL
levels for ease of interfacing. Two enable pins are provided
that also accept the standard TTL and DTL levels. Each
enable controls 2 channels and when an enable pin is disabled (tied low), the corresponding outputs are forced to the
TRI-STATE® condition. If the enable pins are not connected
(i.e., floating), the circuit will function as if it has been enabled. Separate pins are provided for the main power supply
(pin 8), and the logic supply (pin 16). This allows a lower
voltage to be used to bias up the logic resulting in reduced
power dissipation. The chip is packaged in a specially de-

signed 16 pin power DIP. The 4 center pins of this package
are tied together and form the die paddle inside the package. This provides much better heat sinking capability than
most other DIP packages available. The device is capable
of operating at voltages up to 36 volts.

Features
•
•
•
•
•
•

1A output current capability per channel
Pin for pin replacement for L2938
Special 16 pin power DIP package
36 volt operation
Internal thermal overload protection
Logical "0" input voltage up to 1.5 volts results in high
noise immunity

Typical Connection
1-'---.

LM18293

vs ____--------------------------------~--...

TL/H/B706-1

FIGURE 1. Application circuit showing bidirectional and on/off control of a single DC motor
using two outputs and unidirectional on/off function of two DC motors using a single output each.
Order Number LM18293N
NS Package Number N16A

•
4-49

Absolute Maximum Ratings
Peak Output Current (Non-Repetitive t = 5 ms)
2A
Junction Temperature (TJ)
+ 150'C
14'C/W
Thermal Resistance Junction to Case (8Jcl
80'C/W
Thermal Resistance Junction to Ambient (8JA)
Internal Power Dissipation
Internally Limited
Operating Temperature Range
- 40'C to + 125'C
Storage Temperature Range
- 65'C to + 150'C
Lead Temperature (Solder 10 seconds)
260'C

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Output Drive Supply Voltage (Vs)
36V
Logic Supply Voltage (Vss)
36V
Input Voltage (VI)
7V
Enable Voltage (VEl
7V

Electrical Characteristics
Vs

= 24V, Vss = 5V, T = 25'C, L = 0.4V, H = 3.5V, each channel, unless otherwise noted

Symbol

Parameter

Typical

Conditions

Tested Limit
(Note 1)

Design Limit
(Note 2)

Units

Vs

Main Supply (Pin 8)

Maximum Supply Voltage

36

Vmax

Vss

Logic Supply (Pin 16)

Minimum Logic Supply Voltage
Maximum Logic Supply Voltage

4.5
36

Vmin
Vmax

Is

Total Quiescent
Supply Current

VI
VI

=L
=H

10
10

=0
=0

VE = H
VE = H
VE = L

2
16

6
24
4

mAmax
mAmax
mAmax

Iss

Total Quiescent Logic
Supply Current
(pin 16)

VI
VI

=L
=H

10
10

=0
=0

VE = H
VE = H
VE = L

44
16
16

60
22
24

mAmax
mAmax
mAmax

VI

Input Voltage

Min Value of Low
Max Value of Low
Min Value of High
Max Value of High (Vss s: 7)
Max Value of High (Vss > 7)

-0.3
1.5
2.3
Vss
7

Vmin
Vmax
Vmin
Vmax
Vmax

II

input Current

VI
VI

-10
100

/LAmax
/LAmax

-0.3
1.5
2.3
Vss
7

Vmin
Vmax
Vmin
Vmax
Vmax

=L
=H

30

VE

Enable Voltage
(Pins 1, 9)

Min Value of Low
Max Value of Low
Min Value of High
Max Value of High (Vss S:7)
Max Value of High (Vss > 7)

IE

Enable Current

VE
VE

VCE sat Top

Source Saturation
Voltage

VCE sat Bottom

Sink Saturation
Voltage

=L
=H
10 = -1 amp

-30

-100
±10

/LAmax
/LAmax

1.4

1.8

Vmax

= 1 amp

1.2

1.8

Vmax

10

tr

Rise Time

10%-90% Vo

250

ns

tf

Fall Time

90%-10%Vo

250

ns

ton

Turn-On Deiay

50% VI to 50% Vo

450

ns

200
ns
Turn-Off Delay
50% VI to 50% Vo
toff
Note 1: Tested limits are guaranteed and 100% production tested.
Note 2: Design IImlls are guaranteed (bul noll 00% production lesled) over Ihe full supply and lemperature range. These limits are not used to calculate outgoing
quality levels.

4-50

,-----------------------------------------------------------------------------'r
3l:
....
Connection Diagram
Input/Output Truth Table
CD
I\)

'-'"

ENABLE 1

16

INPUT 1

2

15

VSS
INPUT 4

OUTPUT 1

3

14

OUTPUT 4

GROUND

4

13

GROUND

GROUND

5

12

GROUND

OUTPUT 2

6

11

OUTPUT 3

INPUT 2

7

10

Vs

8

9

Enable 1 activates outputs 1 & 2

CD

VE (")

VI (Each Channel)

Va

H
H
L
L

H
L
H
L

H
L
X(O)
X(O)

Co)

(0) High output impedance.
(") Relative to the pertinent channel.

INPUT 3
ENABLE 2
TUH/8706-2

Enable 2 activates outputs 3 & 4

Simplified Schematic

TLlH/8706-3

4-51

~

m
N

co
....

r---------------------------------------------------------------------------------,
Typical Performance Characteristics Vs In all cases =

::E

Output Voltage vs.
Input Voltage

...I

Output Voltage vs•
Enable Voltage

VS-VcrSAT H

'/I I

-+ f2~OC

IF.
1.5

1.0

If,

Y-40OC

I I

VCE~T L

2.0

V,=VE=VSS=5V

l- Tamb=25OC

Tamb =2SOC

J

Saturation Voltage vs.
Output Current

VS-VcrSAT H

V~=VI=5V

"I
I
l-

Vss=Vr.=5V

24V

-+ 12~OC

1.5

::: I-

1.0

~-4OOC

I I

VCE~T L

1.0

2.5

./
VCESAI!--

o

o

2.0

~ ",.

~ VCESAT L

0.5

1.0

1.5

Ia{A)

Source Saturation Voltage
vs. Ambient Temperature
3D

V,=VE=VSS=SV

~1.0A

.....

la=O.5A
la=O.IA

50

~:.5A

V,=L, Vr.=H

./

",.

la=I.0A

/

'":Ia.5A

.,.

""

r- ~

r-t

la=r 'A

I

so

52

I

V,=Vr.=VSS=5V

IJ1.SA

~~

o
-so

Quiescent Logic Supply
Currentvs.
Logic Supply Voltage

Sink Saturation Voltage
vs. Ambient Temperature

o
-so

100

40
100

o

10

30

20

vss(V)

Tamb(OC)

TL/H/8706-4

Typical Applications
DC motor controls (with connections to
ground and to the supply voltages)
Vs~

Bidirectional DC motor control

_ _ _ _......

TL/H/8706-5
TL/H/8708-6

Pin
10

Pin
15

M1

H

H

H

Fast Motor Stop

Run

VE

H

H

L

Fast Motor Stop

Fast Motor Stop

H

L

H

Run

Run

H

L

L

Run

Fast Motor Stop

L
L

= Low

X
H

Free Running
Motor Stop

X

= High

X

= Don"

Inputs

M2

Pin10 = H
Pin15=L
VE = H

VE = L

Free Running
Motor Stop

4-52

TurnCW

Pin10=L
Pin 15 = H

TurnCCW

Pin 10 = Pin 15

Fast Motor Stop

Pin 10 = X
Pin 15 = X

Free Running
Motor Stop

L = Low H = High X = Don" care

care

Function

,-----------------------------------------------------------------------------'r
is:
.....

Motor Control Block Diagram

Bipolar Stepping Motor Control

Q)

+Vs

Step Sequencing Tables

~

fD

Co)

Full Step'
VIN 1

Step

VIN2

L

L

1

L

H

2

H

H

3

H

L

4

L

L

1

r-+--CK 1-+-1-0 vIN1

'VE 1 and VE 2 = H
Half Step
VE 1

H

~

Step

VE2

VIN 1

VIN2

H

L

L

X

1

H

H

L

L

2

L

H

X

L

3

H

H

H

L

4

H

L

H

X

5

H

H

H

H

6

L

H

X

H

7

H

H

L

H

8

H

L

L

X

1

High

L

~

Low

X

~

TL/H/B706-7

Don't care

Mounting Instructions
The junction to ambient thermal resistance of the LM18293
can be reduced by soldering the ground pins to a suitable
copper area of the printed circuit board or to an external
heatsink. The graph below, which shows the maximum power dissipated and junction to ambient thermal resistance as
a function of the side "I" of two equal square copper areas
having a thickness of 35/L, illustrates this. In addition, it is
possible to use an external heatsink (see illustration below).
During soldering the pins temperature must not exceed
230"C and the soldering time must not be longer than 12
seconds. The external heatsink or printed circuit copper
area must be connected to electrical ground.

P.C. BOARD

TL/H/B706-B

Staver External Heat-sink
Maximum power dissipated
and junction to ambient
thermal resistance vs. size
e'
TJ = t5O"C
.J
~ 250 1-t-'-+-+-+-+..o"F"-+-1
;

Z» 1-+-l--I-:7'F-"'+-If-+-l

1/

o tSO

} 100 1""""-1-+-+-+-+-+-+-1
I~'
1.5

z.o

2.5 3.0

3.5

RDS(ON)va
Supply Voltage

ROS(ON) va Temperature

4.0 04.5 5JJ

FlAG CURRENT (mA)

Supply Current va
Supply Voltage

Z'

)~

e 1.4
~

fil

~

1.2

0

I

Z'
0

~

1.0

i

,.11'

0

z

on

" 0,36
=

/

o.a
~
o.a

-55 -35 -15 5 25 <15 liS B5 105
JUNCTION TEMPERATURE (ot)

IW
0.32

1'1..
I"

....

-

11'0.. .......
LO-SIOE

0,31
0.30

125

I I
10 15

Supply Current va
Frequency (Vs = 42V)

2O...-...--.---,r---r--r-...,

\

0.35

0.34

20

25

30 35 olD <15 50
SUPPLY VOLTAGE

55

Supply Current va
Temperature (Vs = 42V)
lBr-r-r--r--r--r-"'-"T"~

lB r---r-f'"T"lTT'rrr-"T"T"T"T'M'1'T1
171--I-1-H+t+H-+++~1fl

i
~

6

lB +-.01:-++-+-+-+-+--1

1'.....

14+-+-~~+--I-+-+~

............

12 t-t-t--I---t--N;:-t--l

1'",,-

~ 10 +-+-+-+-+--I-+--t--"'l
.....
iil

B+-+-+-+-+-+-~~~
6~4-~~~-4

10 20 30 olD 50
SUPPLY VOLTAGE (VOLTS)

6D

10

100

-liS -30 -S 20 45

~~

120 145

JUNCTION TEMPERATURE (ot)

SWITCHING FREQUENcY (kHz)

Current Sense Output
va Load Current

__

70 95

Current Sense
Operating Region
4.Or-~--"T"--r---r---~
3.5r--+--~--~-+--~

o.al--+--+--+--~~
0.0

o.a

1.0 1.5 2.G 2.5
LOAD CURRENT (AMPS)

~~~~~~~~~~

25

3.0

50

75

100

125

150

JUNCTION TEMPERATURE (ot)

TLlH/l05B8-3

4-63

Q)

Q

Pinout Description (See Connection Diagram)

Application Information

Pin 1, BOOTSTRAP 1 Input: Bootstrap capaCitor pin for
half H-bridge number 1. The recommended capacitor
(10 nF) is connected between pins 1 and 2.

TYPES OF PWM SIGNALS
The LMD18200 readily interfaces with different forms of
PWM signals. Use of the part with two of the more popular
forms of PWM is described in the following paragraphs.
Simple, locked anti-phase PWM consists of a single, variable duty-cycle signal in which is encoded both direction
and amplitude information. A 50% duty-cycle PWM signal
represents zero drive, since the net value of voltage (integrated over one period) delivered to the load is zero. For the
LMD18200, the PWM signal drives the direction input (pin 3)
and the PWM input (pin 5) is tied to logic high.

Pin 2, OUTPUT 1: Half H-bridge number 1 output.
Pin 3, DIRECTION Input: See Table I. This input controls
the direction of current flow between OUTPUT 1 and OUTPUT 2 (pins 2 and 10) and, therefore, the direction of rotation of a motor load.
Pin 4, BRAKE Input: See Table I. This input is used to
brake a motor by effectively shorting its terminals. When
braking is desired, this input is taken to a logic high level
and it is also necessary to apply logic high to PWM input, pin
5. The drivers that short the motor are determined by the
logiC level at the DIRECTION input (Pin 3): with Pin 3 logic
high, both current sourcing output transistors are ON; with
Pin 3 logic low, both current sinking output transistors are
ON. All output transistors can be turned OFF by applying a
logiC high to Pin 4 and a logic low to PWM input Pin 5; in this
case only a small bias current (approximately -1.5 mAl exists at each output pin.

Sign/magnitude PWM consists of separate direction (Sign)
and amplitude (magnitude) signals. The (absolute) magnitude signal is duty-cycle modulated, and the absence of a
pulse signal (a continuous logic low level) represents zero
drive. Current delivered to the load is proportional to pulse
width. For the LMD18200, the DIRECTION input (pin 3) is
driven by the sign signal and the PWM input (pin 5) is driven
by the magnitude signal.
USING THE CURRENT SENSE OUTPUT
The CURRENT SENSE output (pin 8) has a sensitivity of
377 /LA per ampere of output current. For optimal accuracy
and linearity of this signal, the value of voltage generating
resistor between pin 8 and ground should be chosen to limit
the maximum voltage developed at pin 8 to 5V, or less. The
maximum voltage compliance is 12V.
It should be noted that the recirculating currents (free
wheeling currents) are ignored by the current sense circuitry. Therefore, only the currents in the upper sourcing outputs are sensed.

Pin 5, PWM Input: See Table I. How this input (and DIRECTION input, Pin 3) is used is determined by the format of the
PWM Signal.
Pin 6, Vs Power Supply
Pin 7, GROUND Connection: This pin is the ground return,
and is internally connected to the mounting tab.
Pin 8, CURRENT SENSE Output: This pin provides the
sourcing current sensing output signal, which is typically
377/LAtA.
Pin 9, THERMAL FLAG Output: This pin provides the thermal warning flag output Signal. Pin 9 becomes active-low at
145·C (junction temperature). However the chip will not shut
itself down until 170·C is reached at the junction.
Pin 10, OUTPUT 2: Half H-bridge number 2 output.

USING THE THERMAL WARNING FLAG
The THERMAL FLAG output (pin 9) is an open collector
transistor. This permits a wired OR connection of thermal
warning flag outputs from multiple LMD18200's, and allows
the user to set the logic high level of the output signal swing
to match system requirements. This output typically drives
the interrupt input of a system controller. The interrupt service routine would then be designed to take appropriate
steps, such as reducing load currents or initiating an orderly
system shutdown. The maximum voltage compliance on the
flag pin is 12V.

Pin 11, BOOTSTRAP 2 Input: Bootstrap capaCitor pin for
Half H-bridge number 2. The recommended capacitor
(10 nF) is connected between pins 10 and 11.
TABLE 1_ LogiC Truth Table
PWM

Dir

Brake

H
H
L
H
H
L

H
L

L
L
L
H
H
H

X
H
L

X

Active Output Drivers
Source 1, Sink 2
Sink 1, Source 2
Source 1, Source 2
Source 1, Source 2
Sink I, Sink 2
NONE

SUPPLY BYPASSING
During switching transitions the levels of fast current changes experienced may cause troublesome voltage transients
across system stray inductance.

Locked Anti-Phase PWM Control

DIRECTiON
(PIN 3)

Sign/Magnitude PWM Control

::nnf JLJ
50~

DUTY CYCLE

AVERAGE LOAD
CURRENT = 0

75~

DUTY CYCLE

25:1 DUTY CYCLE

DIRECTION 5Y
(pR") 0

L._ _ _ _ _ _ __

(P~~~ ill Jlm

RFlli

AVERAGE LOAD CURRENT
FLOWS FRO~ OUTPUT 1
TO OUTPUT 2

-------'1

illJlm

V,,-V +V'JUlLill
02

:V~

AVERAGE LOAD CURRENT
FLOWS FROM OUTPUT 2
TO OUTPUT 1

MOTOR SPEED:

TLlH/l0568-4

. ..- --

---

SLOW

rAST

"EDIU.

AVERAGf CURRENT FLOWS fRON
OUTPUT I TO OUTPUT 2

-------1rllTm-SLOW

MEDIUM

rAST

AVERAGE CURRENT FLOWS F'Rot.I
OUTPUT 2 TO OUTPUT I

TL/H/l0568-5

4-64

Application Information

(Continued)
It is normally necessary to bypass the supply rail with a high
quality capacitor(s) connected as close as possible to the
Vs Power Supply (Pin 6) and GROUND (Pin 7). A 1 JLF highfrequency ceramic capacitor is recommended. Care should
be taken to limit the transients on the supply pin below the
Absolute Maximum Rating of the device. When operating
the chip at supply voltages above 40V a voltage suppressor
(transorb) such as P6KE62A is recommended from supply
to ground. Typically the ceramic capacitor can be eliminated
in the presence of the voltage suppressor. Note that when
driving high load currents a greater amount of supply bypass
capacitance (in general at least 100 JLF per Amp of load
current) is required to absorb the recirculating currents of
the inductive loads.

some precautions are in order. Proper heat sink design is
essential and it is normally necessary to heat sink the Vee
supply pin (pin 6) with 1 square inch of copper on the PCB.
INTERNAL CHARGE PUMP AND USE OF BOOTSTRAP
CAPACITORS
To turn on the high-side (sourcing) DMOS power devices,
the gate of each device must be driven approximately 8V
more positive than the supply voltage. To achieve this an
internal charge pump is used to provide the gate drive voltage. As shown in Figure 1, an internal capaCitor is alternately switched to ground and charged to about 14V, then
switched to V supply thereby providing a gate drive voltage
greater than V supply. This switching action is controlled by
a continuously running internal 300 kHz oscillator. The rise
time of this drive voltage is typically 20 JLs which is suitable
for operating frequencies up to 1 kHz.
For higher Switching frequencies, the LMD18200 provides
for the use of external bootstrap capaCitors. The bootstrap
prinCiple is in essence a second charge pump whereby a
large value capacitor is used which has enough energy to
quickly charge the parasitiC gate input capaCitance of the
power device resulting in much faster rise times. The switching action is accomplished by the power switches themselves (Figure 2). External 10 nF capaCitors, connected
from the outputs to the bootstrap pins of each high-side
switch provide typically less than 100 ns rise times allowing
switching frequencies up to 500 kHz.

CURRENT LIMITING
Current limiting protection circuitry has been incorporated
into the design of the LMD18200. With any power device it
is important to consider the effects of the substantial surge
currents through the device that may occur as a result of
shorted loads. The protection circuitry monitors this increase in current (the threshold is set to approximately 10
Amps) and shuts off the power device as quickly as possible
in the event of an overload condition. In a typical motor
driving application the most common overload faults are
caused by shorted motor windings and locked rotors. Under
these conditions the inductance of the motor (as well as any
series inductance in the Vee supply line) serves to reduce
the magnitude of a current surge to a safe level for the
LMD18200. Once the device is shut down, the control circuitry will periodically try to turn the power device back on.
This feature allows the immediate return to normal operation in the event that the fault condition has been removed.
While the fault remains however, the device will cycle in and
out of thermal shutdown. This can create voltage transients
on the Vee supply line and therefore proper supply bypassing techniques are required.
The most severe condition for any power device is a direct,
hard-wired ("screwdriver") long term short from an output to
ground. This condition can generate a surge of current
through the power device on the order of 15 Amps and
require the die and package to diSSipate up to 500 Watts of
power for the short time required for the protection circuitry
to shut off the power device. This energy can be destructive, particularly at higher operating voltages (> 30V) so

INTERNAL PROTECTION DIODES
A major consideration when Switching current through inductive loads is protection of the switching power devices
from the large voltage transients that occur. Each of the four
switches in the LMD18200 have a built-in protection diode
to clamp transient voltages exceeding the positive supply or
ground to a safe diode voltage drop across the switch.
The reverse recovery characteristics of these diodes, once
the transient has subsided, is important. These diodes must
come out of conduction quickly and the power switches
must be able to conduct the additional reverse recovery current of the diodes. The reverse recovery time of the diodes
protecting the sourcing power devices is typically only 70 ns
with a reverse recovery current of 1A when tested with a full
6A of forward current through the diode. For the sinking
devices the recovery time is typically 100 ns with 4A of reverse current under the same conditions.

+Vs

+Vs

~-:~~-.

TO GATE

TO GATE
DRIVE
CIRCUIT

-1

DRIVE "'--f--
(.)

/

./

2

It:

e0
2

V

....~
o
o

I'

/'
2

/

3

..

5

6

7

8

VCURRENT ADJUST (VOLTS)
TLlH/l056B-13

4-68

ri:

Typical Applications (Continued)

c....
co

VELOCITY REGULATION
Utilizes tachometer output from the motor to sense motor speed for a locked anti-phase control loop.
DIRECTION CONTROL

+10V

N

o
o

12V TO 30V

L.r

15 13
16
11

2

LM3525A

LMD1820D

o TO 7400 RPM

1

30V DC MOTOR

VSPEED
ADJUST

11
lk

10
2

9

+
4

7

10k

=

5.1k

VlACH
1000 RPM/V

TL/H/1056B-14

Motor Speed vs
Control Voltage
8000

il
6000

I

J

1/
I

2000

o
o

I

/
I
1

2

3

4

VSPEED (VOLTS)
TLlH/l056B-15

4-69

....
~ ~National
~

:5

~ Semiconductor

LMD18201 3A, 55V H-Bridge
•
•
•
•
•

TTL and CMOS compatible inputs
No "shoot-through" current
Thermal warning flag output at 145·C
Thermal shutdown (outputs off) at 170·C
Internal clamp diodes
II Shorted load protection
• Internal charge pump with external bootstrap capability

General Description
The LMD18201 is a SA H-Bridge designed for motion control applications. The device is built using a multi-technology
process which combines bipolar and CMOS control circuitry
with DMOS power devices on the same monolithic structure. The H-Bridge configuration is ideal for driving DC and
stepper motors. The LMD18201 accommodates peak output currents up to 6A. Current sensing can be achieved via
a small sense resistor connected in series with the power
ground lead. For current sensing without disturbing the path
of current to the load,. the LMD18200 is recommended.

Applications
•
•
•
•
•

Features
• Delivers up to SA continuous output
• Operates at supply voltages up to 55V
• Low AOS(ON) typically O.SSO per switch

DC and stepper motor drives
Position and velocity servomechanisms
Factory automation robots
Numerically controlled machinery
Computer printers and plotters

Functional Diagram
THERMAL FLAG OUTPUT

BOOTSTRAP 1

OUTPUT 1

1

2

Ys
6

OUTPUT 2

BOOTSTRAP 2

10

11

THERMAL
SENSING
UNDERYOLTAGE
LOCKOUT

DIRECTION 3
BRAKE 4
PWM 5

7
Power Ground/Sense

8
Signal Ground

TLlH/l0793-1

Connection Diagram and Ordering Information
11

BOOTSTRAP 2

10

OUTPUT 2
THERMAL FLAG OUTPUT
SIGNAL GROUND

o

POWER GROUND/SENSE
Ys POWER SUPPLY
PWM INPUT
BRAKE INPUT
DIRECTION INPUT
OUTPUT 1

1.

BOOTSTRAP I

MOUNTING TAB CONNECTED TO GROUND (PIN 7)
TLlH/l0793-2

Top View
4-70

Order Number LMD18201T
See NS Package NumberTA11B

Absolute Maximum Ratings

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Total Supply Voltage (Vs, Pin 6)
60V
Voltage at Pins 3, 4, 5 and 9
12V
Voltage at Bootstrap Pins (Pins 1 and 11)
VOUT + 16V
Peak Output Current (200 ms)
6A
Continuous Output Current (Note 2)
3A
Power Dissipation (Note 3)
25W
Sense Voltage (Pin 7 to Pin 8)
+0.5Vto -1.0V

Power Dissipation (TA = 25·C, Free Air)
3W
150·C
Junction Temperature, TJ(max)
ESD Susceptibility (Note 4)
1500V
- 65·C to + 150·C
Storage Temperature, TSTG
300·C
Lead Temperature (Soldering, 10 sec.)

Operating Ratings (Note 1)
- 40·C to + 125·C
+12Vto +55V

Junction Temperature, TJ
Vs Supply Voltage

Electrical Characteristics
The following specifications apply for Vs = 42V, unless otherwise specified. Boldface limits apply over the entire operating
temperature range, -40·C :s: TJ :s: + 125·C, all other limits are for TA = TJ = 25·C. (Note 5)
Symbol

Parameter

ROS(ON)

Switch ON Resistance

Conditions

Typ

Limit

Units

= 3A (Note 6)

0.33

0.4/0.8

ROS(ON)

Switch ON Resistance

Output Current = 6A (Note 6)

0.33

0.4/0.8

o (max)
o (max)

VCLAMP

Clamp Diode Forward Drop

Clamp Current

= 3A (Note 6)

1.2

1.5

V (max)

VIL

Logic Low Input Voltage

Pins 3, 4, 5

-0.1
0.8

V (min)
V (max)

IlL

Logic Low Input Current

VIN

-10

".A(max)

VIH

Logic High Input Voltage

Pins 3, 4, 5

2
12

V (min)
V (max)

Logic High Input Current

VIN = 12V, Pins = 3,4,5

10

".A(max)

Undervoltage Lockout

Outputs Turn OFF

9
11

V (min)
V (max)

IlL

Output Current

= -O.W, Pins = 3,4,5

Pin 9 :s: O.BV, IL

0.15

Flag Output Leakage

= 2 mA
= TJW, IL = 2 mA
VF = 12V

145

TJ

Shutdown Temperature

Outputs Turn OFF

170

TJW

Warning Flag Temperature

VF(ON)

Flag Output Saturation Voltage

IF(OFF)
TJSO

0.2

13

'C
V
10

".A(max)
·C

Is

Quiescent Supply Current

All Logic Inputs Low

to(ON)

Output Turn-On Delay Time

Sourcing Outputs, lOUT = 3A
Sinking Outputs, lOUT = 3A

300
300

25

mA(max)
ns
ns

tON

Output Turn-On Switching Time

Bootstrap Capacitor = 10 nF
Sourcing Outputs, lOUT = 3A
Sinking Outputs, lOUT = 3A

100
80

ns
ns

to(OFF)

Output Turn-Off Delay Times

Sourcing Outputs, lOUT = 3A
Sinking Outputs, lOUT = 3A

200
200

ns
ns

tOFF

Output Turn-Off Switching Times

Bootstrap Capacitor = 10 nF
Sourcing Outputs, lOUT = 3A
Sinking Outputs, lOUT = 3A

75
70

ns
ns

1

".a

20

".s

tpw

Minimum Input Pulse Width

Pins 3, 4 and 5

tCPR

Charge Pump Rise Time

No Bootstrap Capacitor

4-71

•

Electrical Characteristics (Continued)
Note 1: Absolute Maximum Ratings indicate limns beyond which damage to the davloa may occur. OC and AC electrical speciflcations do not apply when operating
the devioa beyond ils rated operating condRions.
Note 2: See Application Information for details regarding current limiting.
Note 3: The maximum power dissipation must be derated at elevated temperatures and is a function of TJ(max), 9JAo and TA. The maximum allowable power
dissipation at any temperature is po(max) = (TJ(max) - TAl/9JA, or the number given in the Absolute Ratings, whichever is lower. The typical thermal resistance
from junction to case (9Jcl is Ul"CIW and from junction 10 ambient (8JAl is 3fY'C/W. For guaranteed operation TJ(max) = 12S'C.
Note 4: Human-body model, 100 pF discharged through a 1.5 kll resistor. Except Bootstrap pins (pins 1 and 11) which are protected to 1000V of ESO.
Note 5: Alilimils are 100% production tested at 2S'C. Temperature extreme limits are guaranteed via correlation using acoapled sac (Statistical Quality Control)
methods. All limits are used to calculate AOQL, (Average Outgoing Quality Level).
Note 6: Output currents are pulsed (tw < 2 ms, Duty Cycle < 5%).

Typical Performance Characteristics
VSAT vs Flag Current

S
.§.

3SO

1.8

300

1.8

TJ

= lSOOC

~

~

200

.

~

>

V

150
100

L

~

)1'

,/

2SO

V

V
V

V'

.....
Il6

4.5 s.o

4J)

-55 -35 -15 5 2S 045 65

FLAG CURRENT (mA)

~

.

OUJUTS H!

A~

10

30

40

I

"- r-

so

SUPPLY VOLTAGE (VOlTS)

60

La-SIDE

I 1\

10 IS 20 25 30 35 40 045

55

Supply Current va
Temperature (Vs = 42V)
18
16

16

14

Il!

IS

12

i.

14

lL'

.......

......

I ' .......

'"

10

13
12
1

so

SUPPLY VOLTAGE

18

_f-

I--'

.......t-'"
I I

105 125

17

0

OUTPUTS LOW

20

I"

!

ffi

V

/
1/

as

I I
I I
I I
HI-SIDE

\

=

16

it
::>

.

Supply Current va
Fnequency(Vs
42V)

20

12

IL = 3A
TJ = 250C

JUNCTION TEMPERAlURE (OC)

Supply Current va
Supply Voltage

!....
i0

OAO
0.39
0.38
0.37
::E
5 0.36
0.35
%'
0.34
'" 0.33
0.32
0.31
0.30

~

1,..-'1"

1.5 2.0 2.5 3.0 3.5

ROS(ON)VS
Supply Voltage

ROS(ON) va Temperature

.......

6

10

100

SWITCHING rREQUENCY (kHz)

-ss -30

-5 20 045 70 95 120 1045

JUNCTION TEMPERAlURE (OC)

TUH/l0793-3

Switching Time Definitions

Test Circuit
10 nF

+5V
+5V

INPUT

DIR

BRAKE

-

INPUT

PWM

3A
SOURCE

0
N

co

Q

::Iii

...J

SINK

3A
O.3V
SENSE

TUH/l0793-9

TUH/l0793-8

4-72

Pinout Description

Application Information

(See Connection Diagram)

Pin 1, BOOTSTRAP 1 Input: Bootstrap capacitor pin for
half H-Bridge number 1. The recommended capacitor
(10 nF) is connected between pins 1 and 2.

TYPES OF PWM SIGNALS

Pin 3, DIRECTION Input: See Table I. This input controls
the direction of current flow between OUTPUT 1 and OUTPUT 2 (pins 2 and 10) and, therefore, the direction of rotation of a motor load.

Simple, locked anti-phase PWM consists of a single, variable duty-cycle signal in which is encoded both direction
and amplitude information. A 50% duty-cycle PWM signal
represents zero drive, since the net value of voltage (integrated over one period) delivered to the load is zero. For the
LMD18201, the PWM signal drives the direction input (pin 3)
and the PWM input (pin 5) is tied to logic high.

Pin 4, BRAKE Input: See Table I. This input is used to
brake a motor by effectively shorting its terminals. When
braking is desired, this input is taken to a logic high level
and it is also necessary to apply logic high to PWM input, pin
5. The drivers that short the motor are determined by the
logic level at the DIRECTION input (Pin 3): with Pin 3 logic
high, both current sourcing output transistors are ON; with
Pin 3 logic low, both current sinking output transistors are
ON. All output transistors can be turned OFF by applying a
logic high to Pin 4 and a logic low to PWM input Pin 5; in this
case only a small bias current (approximately -1.5 mAl exists at each output pin.

Sign/magnitude PWM consists of separate direction (sign)
and amplitude (magnitude) signals. The (absolute) magnitude signal is duty-cycle modulated, and the absence of a
pulse signal (a continuous logic low level) represents zero
drive. Current delivered to the load is proportional to pulse
width. For the LMD18201, the DIRECTION input (pin 3) is
driven by the sign signal and the PWM input (pin 5) is driven
by the magnitude signal.
USING THE THERMAL WARNING FLAG

Pin 5, PWM Input: See Table I. How this input (and DIRECTION input, Pin 3) is used is determined by the format of the
PWM Signal.

The THERMAL FLAG output (pin 9) is an open collector
transistor. This permits a wired OR connection of thermal
warning flag outputs from multiple LMD18201's, and allows
the user to set the logic high level of the output signal swing
to match system requirements. This output typically drives
the interrupt input of a system controller. The interrupt service routine would then be designed to take appropriate
steps, such as reducing load currents or initiating an orderly
system shutdown. The maximum voltage compliance on the
flag pin is 12V.

Pin 6, Vs Power Supply
Pin 7, POWER GROUND/SENSE Connection: This pin is
the ground return for the power DMOS transistors of the HBridge. The current through the H-Bridge can be sensed by
adding a small, 0.1 n, sense resistor from this pin to the
power supply ground.
Pin 8, SIGNAL GROUND: This is the ground return for the
internal logic circuitry used to control the PWM switching of
the H-Bridge.

SUPPLY BYPASSING
During switching transitions the levels of fast current changes experienced may cause troublesome voltage transients
across system stray inductances.

Pin 9, THERMAL FLAG Output: This pin provides the thermal warning flag output signal. Pin 9 becomes active-low at
145'C (junction temperature). However the chip will not shut
itself down untii 170'C is reached at the junction.

It is normally necessary to bypass the supply rail with a high
quality capacitor(s) connected as close as possible to the
Vs Power Supply (Pin 6) and POWER GROUND (Pin 7). A
1 ,..F high-frequency ceramic capacitor is recommended.
Care should be taken to limit the transients on the supply
pin below the Absolute Maximum Rating of the device.
When operating the chip at supply voltages above 40V a
voltage suppressor (transorb) such as P6KE62A is recommended from supply to ground. Typically the ceramic capacitor can be eliminated in the presence of the voltage
suppressor. Note that when driving high load currents a
greater amount of supply bypass capacitance (in general at
least 100 ,..F per Amp of load current) is required to absorb
the recirculating currents of the inductive loads.

Pin 10, OUTPUT 2: Half H-Bridge number 2 output.
Pin 11, BOOTSTRAP 2 Input: Bootstrap capacitor pin for
half H-Bridge number 2. The recommended capacitor
(10 nF) is connected between pins 10 and 11.
TABLE I. Logic Truth Table
Dir

Brake

H
H
L
H
H
L

H
L

L
L
L
H
H
H

X
H
L

X

Active Output Drivers
Source 1, Sink 2
Sink 1, Source 2
Source 1, Source 2
Source 1, Source 2
Sink 1, Sink 2
NONE

Sign/Magnitude PWM Control

I

~

DIRECTION

Locked Anti-Phase PWM Control

~(~~
V"-V,,

(PIN'),

::Jl ru JLJ
50" DUTY CYCL£

75% DlITY CYa!

(PI~:V ill

:::* Rf ill
AVERAGE LOAD

AVERAGE LOAD CURRENT

AVERAGE LOAD C1JRRENT

CURREHT=O

FLOWS FROM OUTPUT 1
TO OUTPUT 2

FLOWS FROM OUTPUT 2
TO OUTPUT 1

L _ _ _ _ _ _ __

ill Jlm
v"-V,, +VSJUJlill
,................·lIT1fill·

25'-1: DUTY CYa.E

Jlm

-Vs

MOTOR SPEED:

SLOW

.ED..

FAST

AVruGE CURRENT FlOWS FRO'"
OUTPUT 1 TO OUTPUT 2

TlIH/l0793-4

SLOW

MEDIUM

AVERAGE: CURRENT

FAST

nows FROtoi

OUTPUT 2 TO OUTPUT 1

TlIH/l0793-5

4-73

....cCD
o....
I\)

The LMD18201 readiiy interfaces with different forms of
PWM signals. Use of the part with two of the more popular
forms of PWM is described in the following paragraphs.

Pin 2, OUTPUT 1: Half H-Bridge number 1 output.

PWM

r3:

9-

~
co
9C

:e
-I

~-----------------------------------------------------------------------------------------,

Application Information

(Continued)

CURRENT LIMITING
Current limiting protection circuitry has been incorporated
into the design of the LMD18201. With any power device it
is important to consider the effects of the substantial surge
currents through the device that may occur as a result of
shorted loads. The protection circuitry monitors the current
through the upper transistors and shuts off the power device as quickly as possible In the event of an overload condition (the threshold is set to approximately lOA). In a typical motor driving application the most common overload
faults are caused by shorted motor windings and locked
rotors. Under these conditions the inductance of the motor
(as well as any series inductance in the Vee supply line)
serves to reduce the magnitude of a current surge to a safe
level for the LMD18201. Once the device Is shut down, the
control circuitry will periodically try to turn the power device
back on. This feature allows the immediate return to normal
operation once the fault condition has been removed. While
the fault remains however, the device will cycle in and out of
thermal shutdown. This can create voltage transients on the
Vee supply line and therefore proper supply bypassing techniques are required.
The most severe condition for any power device Is a direct,
hard-wired ("screwdriver") long term short from an output to
ground. This condition can generate a surge of current
through the power device on the order of 15 Amps and
require the die and package to dissipate up to 500W of
power for the short time required for the protection circuitry
to shut off the power device. This energy can be destructive, particularly at higher operating voltages (>SOV) so
some precautions are In order. Proper heat sink design is
essential and it Is normally necessary to heat sink the Vee
supply pin (pin 6) with 1 square inch of copper on the PC
board.

INTERNAL CHARGE PUMP AND USE OF
BOOTSTRAP CAPACITORS
To turn on the high-side (sourcing) DMOS power devices,
the gate of each device must be driven approximately 8V
more positive than the supply voltage. To achieve this an
internal charge pump is used to provide the gate drive voltage. As shown in Figure 1, an internal capacitor is alternately switched to ground and charged to about 14V, then
switched to Vs thereby providing a gate drive voltage greater than Vs. This switching action is controlled by a continuously running internal SOO kHz oscillator. The rise time of
this drive voltage is typically 20 /Ls which is suitable for operating frequencies up to 1 kHz.
For higher switching frequencies, the LMD18201 provides
for the use of external bootstrap capacitors. The bootstrap
principle Is in essence a second charge pump whereby a
large value capacitor is used which has enough energy to
quickly charge the parasitic gate input capacitance of the
power device resulting in much faster rise times. The switching action is accomplished by the power switches themselves (Figure 2). External 10 nF capacitors, connected
from the outputs to the bootstrap pins of each high-side
switch provide typically less than 100 ns rise times allowing
switching frequencies up to 500 kHz.
INTERNAL PROTECTION DIODES
A major consideration when switching current through inductive loads Is protection of the switching power devices
from the large voltage transients that occur. Each of the four
switches in the LMD18201 have a built-in protection diode
to clamp transient voltages exceeding the positive supply or
ground to a safe diode voltage drop across the switch.
The reverse recovery characteristics of these diodes, once
the transient has subsided, is Important. These diodes must
come out of conduction quickly and the power switches
must be able to conduct the additional reverse recovery current of the diodes. The reverse recovery time of the diodes
protecting the sourcing power devices is typically only 70 ns
with a reverse recovery current of 1A when tested with a full
SA of forward current through the diode. For the sinking
devices the recovery time is typically 100 ns with 4A of reverse current under the same conditions.

tVs

tVs

.....-11-1....- .

TO GATE
DRIVE
CIRCUIT

TO GATE
DRIVE +---+-~
CIRCUIT

--1

GROUND

.......-..I--<>,
EXTERNAL
BOOTSTRAP
CAPACITOR

GROUND
TL/H/10793-6
TL/H/10793-7

FIGURE 1_ Internal Charge Pump Circuitry

FIGURE 2. Bootstrap Circuitry

4-74

r-----------------------------------------------------------------------------'r

s::
CI

Typical Applications
To sense the bridge current through the LMD18201 requires
the addition of a small sense resistor between the power
ground/sense pin (Pin 7) and the actual circuit ground. This
resistor should have a value of 0.10 or less to stay within
the allowable voltage compliance of the sense pin, particularly at higher operating current levels. The voltage between
power ground/sense (Pin 7) and the signal ground (Pin 8)
must stay within the range of -1V to +0.5V. Internally
there is approximately 250 between pins 7 and 8 and this
resistance will slightly reduce the value of the external
sense resistor. Approximately 70% of the quiescent supply
current (10 rnA) flows out of pin 7. This will cause a slight
offset to the voltage across the sense resistor when the
bridge is not conducting. During reverse recovery of the internal protection diodes the voltage compliance between
pins 7 and 8 may be exceeded. The duration of these spikes
however are only approximately 100 ns and do not have
enough time or energy to disrupt the operation of the
LMD18201.

BASIC MOTOR DRIVER

The LMD18201 can directly interface to any Sign/Magnitude PWM controller. The LM629 is a motion control processor that outputs a Sign/Magnitude PWM signal to coordinate either positional or velocity control of DC motors. The
LMD18201 provides fully protected motor driver stage.
CURRENT SENSING

In many motor control applications it is desirable to sense
and control the current through the motor. For these types
of applications a companion product, the LMD18200, is also
available. The LMD18200 is identical to the LMD18201 but
has current sensing transistors that output a current directly
proportional to the current conducted by the two upper
DMOS power devices to a separate current sense pin. This
technique does not require a low valued, power sense resistor and does not subtract from the available voltage drive to
the motor.

Basic Motor Driver
+5V
10k

Motor Voltage

9

6

IRQ
Host

8

p.C

Bus

Sign

Dir

3

Magnitude

PWM

5

LMD18201

LM629

Motor

11

Encoder

2 or 3

TL/H/l0793-10

Current Sensing
+55V
Vs

Direction ----1~3-99~-~6r--*;.;;.;.;;..........- _ .
PWM
5
Brake
4
1
+5V
LMD1B201
11

Molor

10k
Thermal Flag ........-

... 9

101----,-+--...1

8

7

0.1D.

,---+VSENSE
o 10 0.3V for up 10
3A of Bridge Currenl
TLlH/l0793-11

4-75

...
...o

CIC)

N

Section 5
Peripheral Drivers

•

Section 5 Contents
Peripheral Orivers-Introduction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . • .
Peripheral Orivers-Selection Guide ............. . . . . . • . . . . .. . . . .. . . .. . . . . . . . . . .. . . . . .
OP731 0/0P831 0/0P7311/0P8311 Octal Latched Peripheral Orivers .....................
081631/083631/081632/083632/081633/083633/081634/08363 4 CM08 Oual
Peripheral Orivers ..................................•..... . . . . . . . . . . . . . . . . . . . . . . . .
082001/089665/082002/089666/082003/089667/082004/08966 8 High
CurrentlVoltage Oarlington Orivers ................................... ..............
083654 Printer 8olenoid Oriver ......................................................
083658 Quad High Current Peripheral Oriver. . . . • . . • • . • • . . • . . . . . . • . . . • . . • . . . . . . . . . • . . • •
083668 Quad Fault Protected Peripheral Oriver • . . . . . • . . . . . . . • . . . . . . • . . . . . . . . • . . . • . . . . .
083669 Quad High Current Peripheral Oriver. . . . . . . • . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
083680 Quad Negative Voltage Relay Oriver ...........................•..............
0855451/2/3/4,0875450/1/2/3/4 8eries Oual Peripheral Orivers •..••..•..•.... ,. . . . . . .

5-2

5-3
5-4
5-5
5-12
5-17
5-22
5-26
5-29
5-32
5-35
5-38

~National

~ Semiconductor

Peripheral Drivers
Peripheral drivers is a broad definition given to interface
power devices. The devices generally have open-collector
output transistors that can switch hundreds of milliamps at
high voltage and are driven by standard logic gates. They
serve many applications including relay drivers, printer hammer drivers, lamp drivers, bus drivers, core memory drivers,
voltage level translators, stepper motor drivers and solenoid
drivers.
Unlike standard logic devices, peripheral drivers have many
varied load situations depending on the application. This requires the design engineer to interpret device specifications
in greater detail. Designers at National Semiconductor have
incorporated many technically advanced and useful features Into their broad line of peripheral driver devices.

Some of these features include:
• Short circuit protection at individual outputs
• Glitch-free power up/down
• Fail-safe operation
• Inductive fly-back protection
• Negative transient protection
• High input impedance for CMOS/NMOS compatibility
For further information on National Semiconductor's broad
line of peripheral drivers, refer to the selection guide to follow and application note AN-213 in Appendix H.

•
5-3

Peripheral Drivers Selection Guide

PERIPHERAL DRIVERS SELECTION GUIDE
Device Number and
Temperature Range

O°Cto

+ 70°C

OP8310
OP8311

U1

J,.

-55°C to

+ 125°C

Drivers/
Package

Logic Function
(Driver On)

Input
Compatibility
(Logie)

Output High
Voltage (V)

8
8

(Note 5)
(Note 6)

TIL
TIL

7

NAND

OP7310
OP7311

Latch-Up
Voltage
(Note 3) (V)

Output Low
Voltage (V)

Output Low
Current (rnA)

Propagation
Delay
Typ (ns)

On Power
Supply
Current (rnA)

Page
No.

30
30

0.5
0.5

100
100

40
40

152
125

5-5
5-5

TIL

50

1.6

350

5000

OS2001C
OS9665C
OS2002C
OS9666C
OS2003C
OS9667C
OS2004C
OS9668C

OS2002M
OS9666M
OS2003M
OS9667M
OS2004M
OS9668M

7

NAND

PMOS

50

1.6

350

5000

7

NAND

TIL/CMOS

50

1.6

350

5000

7

NAND

CMOS/PMOS

50

1.6

350

5000

OS3631
OS3632
OS3633
OS3634

OS1631
OS1632
OS1633
OS1634

2
2
2
2

AND
NAND
OR
NOR

CMOS
CMOS
CMOS
CMOS

56
56
56
56

40
40
40
40

1.4
1.4
1.4
1.4

300
300
300
300

150
150
150
150

8
8
8
8

5-12
5-12
5-12
5-12

10
4
4
4

(Note 2)
NAND
NAND
AND

(Note 2)
TILILS
TILILS
TILILS

(Note 1)
70
70
70

45
35
(Note 7)
35

1.6
0.7
1.5
0.7

250
600
600
600

1000
2430
2000

70
65
80
65

5-22
5-26
5-29
5-32

OS3680

4

(Note 4)

TIL/CMOS

-2.1

-60

-60

-50

10,000

4.4

5-35

OS75450
OS75451
OS75452
OS75453
OS75454

2
2
2
2
2

AND
AND
NAND
OR
NOR

TIL
TIL
TIL
TIL
TIL

30
30
30
30
30

20
20
20
20
20

0.7
0.7
0.7
0.7
0.7

300
300
300
300
300

31
31
31
31
31

55
55
55
55
55

5-38
5-38
5-38
5-38
5-38

OS3654
OS3658
OS3668
OS3669

OS55451
OS55452
OS55453
OS55454

5-17
5-17
5-17
5-17
5-17
5-17
5-17
5-17

Note 1: The 083654 contains an internal inductive fly-back clamp circuit connected from the output to ground. As an example, 083654 driving a relay solenoid connected to 28V would clamp the output voltage fly-back transient at SOV
caused by the solenoid's stored inductive current. This clamp protects the circuit output and quenches the fly-back.
Note 2: The 083654 is a 1Q-bit shift register followed by 10 enabled drivers. The input circuit is equivalent to a 4k resistor to ground, and the logic input thresholds are 2.SV and O.SV. The recommended power supply voltage is 7.5V to
9.5V. The circuit can be cascaded to be a 20 or 30-bit shift register.
Note 3: Latch-up voltage is the maximum voltage the output can sustain when switching an inductive load.
Note 4: 053680 has a differential input circuit.
Note 5; 088310 inverting, positive edge latching.
Note 6: D58311 inverting, falllhrough lalch.
Note 7: D53668 35V, lalch-up wilh oulpul faull proleclion.

- -

C

'"tI
.....
w

~National

....

~ Semiconductor

o
.....
C
'"tI
.....
w

.....

DP7310/DP8310/DP7311/DP8311 Octal Latched
Peripheral Drivers

.....
.....
C
'"tI

• All outputs simultaneously sink rated current "DC" with
no thermal derating at maximum rated temperature
• Parallel latching or buffering
• Separate active low enables for easy data bussing
• Internal "glitch free" power up clear
• 10% Vee tolerance

General Description
The DP7310/831 0, DP7311/8311 Octal Latched Peripheral
Drivers provide the function of latching eight bits of data
with open collector outputs, each driving up to 100 mA DC
with an operating voltage range of 30V. Both devices are
designed for low input currents, high input! output voltages,
and feature a power up clear (outputs off) function.

Applications

The DP7310/8310 are positive edge latching. Two active
low writel enable inputs are available for convenient data
bussing without external gating.
The DP7311/8311 are positive edge latches. The active low
strobe input latches data or allows fall through operation
when held at logic "0". The latches are cleared (outputs off)
with a logic "0" on the clear pin.

•
•
•
•
II
•
•
•
•

Features
• High current, high voltage open collector outputs
• Low current, high voltage inputs

High current high voltage drivers
Relay drivers
Lamp drivers
LED drivers
TRIAC drivers
Solenoid drivers
Stepper motor drivers
Level translators
Fiber-optic LED drivers

Connection Diagrams
Dual-In-Llne Package

Dual-In-Line Package

WEl

20

Vee

CUi

20

Vee

014

19

WE2

Dl4

19

STn

013

lB

015

013

lB

Dl5

012

17

016

Dl2

17

016

011

0P731OI 16
oPB31o 15

017

011

OIB

001

0P73111 16
OPB311 15

017
OIB

002

14

oOB

002

14

OOa

003

13

007

003

13

007

004

12

006

12

006

11

005

004
GNO

11

005

001

GNO

10

4

10

TL/F/5246-1

TL/F/5246-2

Top View

Top View
Order Number DP731OJ, DP7311J,
DP8310N or DP8311N
See NS Package Number J20A or N20A

5-5

m
w
o
.....

....
C

'"tI

m

....w
....

Absolute Maximum Ratings (Note 1)

Operating Conditions

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
OHlce/Dlstrlbutors tor availability and speCifications.
Supply Voltage
7.0V
Input Voltage
35V
Output Voltage
35V
Maximum Power Dissipation· at 25·C
Cavity Package
1821 mW
DP8310/DP8311
2005mW
-65·C to + 150·C
Storage Temperature Range
Lead Temperature (Soldering, 4 sec.)
260·C

Supply Voltage (Vee>
Temperature
DP7310/DP7311
DP8310/DP8311
Input Voltage
Output Voltage

Min
4.5

Max
5.5

Units
V

-55
0

+125
+70
30
30

·C
·C
V
V

Max

Units

'Oerale cavity package 12.1 mWl'O above 25'0; derale molded package
16.0 mW/'O above 25'0.

DC Electrical Characteristics DP7310/DP8310, DP7311 IDP8311 (Notes 2 and 3)
Symbol

Parameter

VIH

Logical "1" Input Voltage

VI~

Logical "0" Input Voltage

VO~

Logical "0" Output Voltage
DP7310/DP7311
DP8310/DP8311

IOH

Logical "1" Output Current
DP7310/DP7311
DP8310/DP8311

Conditions

Min

Typ

2.0

V
0.8

V

Data outputs latched to
logical "0", Vee = Min.
IOL = 75mA
lo~ = 100 mA

0.35

0.4
0.5

V
V

Data outputs latched to
logical "1", Vee = Min.
VOH = 25V
VOH = 30V

2.5

500
250

IlA
IlA

IIH

Logical "1" Input Current

VIH

25

IlA

Input Current at Maximum Input
Voltage

VIN

= 2.7V, Vee = Max
= 30V, Vee = Max

0.1

II

1

250

IlA

= 0.4V, Vee = Max

-215

-300

IlA

-0.8

-1.5

V

100
100
88
88

125
152
117
125

mA
mA
mA
mA

40
40
25
25

47
57
34
36

mA
mA
mA
mA

IlL

Logical "0" Input Current

VIN

Vclamp

Input Clamp Voltage

liN = 12 mA

leco

Supply Current, Outputs On

Data outputs latched to a
logical "0". All Inputs are
at logical "1", Vcc = Max.

DP7310
DP8310
DP7311
DP8311
lecl

Supply Current, Outputs Off

Data outputs latched to a
logic "1". Other
conditions same as IceD.

DP7310
DP8310
DP7311
DP8311

5-6

C

'V
......

AC Electrical Characteristics DP7310/DP8310:Vcc = 4.5V, TA = -55'Cto + 125'C
Symbol

Parameter

Conditions

Min

Max

Units

40

120

ns

70

150

ns

(Figure 1)

tpd1

Low to High Propagation Delay
Write Enable Input to Output

(Figure 1)

tSETUP

Minimum Set-Up Time
Data in to Write Enable Input

tHOLD = 0 ns
(Figure 1)

tpWH'
tpWL

Minimum Write Enable Pulse
Width

(Figure 1)

tTHL

High to Low Output Transition Time

(Figure 1)

16

35

tTLH

Low to High Output Transition Time

(Figure 1)

38

70

ns

CIN

"N" Package (Note 4)

5

15

pF

Typ

Max

Units

30

60

ns

70

100

ns

Parameter

20

ns

60

25

ns

Conditions

Min

tpdQ

High to Low Propagation Delay
Data In to Output

(Figure2)

tpd1

Low to High Propagation Delay
Data to Output

(Figure2)

tSETUP

Minimum Set-Up Time
Data in to Strobe Input

tHOLD = Ons
(Figure 2)

0

-25

ns

60

35

ns

tpWL

Minimum Strobe Enable Pulse Width

(Figure 2)

tpdC

Propagation Delay Clear to Data Output

(Figure 2)

tpwc

Minimum Clear Input Pulse Width

(Figure 2)

tTHL

High to Low Output Transition Time

(Figure 2)

20

35

ns

tTLH

Low to High Output Transition Time

(Figure 2)

38

60

ns

70
60

ns
135

25

ns
ns

pF
Input Capacitance-Any Input
(Note 4)
5
15
Note 1: "Absolute Maximum Ratings" are those values beyond which the safety of the device cannot be guaranteed. Except for "Operating Temperature Range"
they are not meant to imply that the devices should be operated at these limits. The table 01 "Electrical Characteristics" provides conditions for actual device
CIN

operation.
Note 2: Unless otherwise specified minimax limits apply across the - SS'C to + 12S'C tempemture range for the DP731 0/DP7311 and across the O'C to + 70'C
for the DP8310/DP8311. All typical values are for TA = 25'C, Vee = SV.

Note 3: All currents into device pins shown as positive, out of device pins as negative, all voltages referenced to ground unless otherwise noted.
Note 4:

Input capacitance is guaranteed by periodic testing. 'TEST

=

10kHz at 300 mV, TA

5-7

=

'V

(j

....

....
.....
C

'V

45

AC Electrical Characteristics DP7311/DP8311:Vcc = 5V, TA = 25'C
Symbol

CI
.....

C

High to Low Propagation Delay
Write Enable Input to Output

tpdo

....

W

Typ

2S'C.

CO

....

w

!::!
c'V
CO
W

....
....

~
~

(I)

~

r------------------------------------------------------------------------------------------,
Logic Table

Q

(:)
~

(I)

~
Q
......
~
~

~
Q

(:)
~

(I)

Ii:
Q

DP7310/DP8310

DP7311/DP8311

Write
Enable 1
WE1

Write
Enable 2
WE2

Data
Input
D11-8

Data
Output
DOl-8

0
0
0
J'"'
J'"'
0
1
1

0
J'"'
J'"'
0
0

X

Q

0
0
1

1
0
1
0

1
0
1

X
X
X

Q
Q
Q

1

Data
Input
D11-8

Data
Output
DOl-8

1
0
0

X

Q

0
1

X

X

1
0
1

Clear
CLR

Strobe
STR

1
1
1
0

X = Don't Care
1 = Outputs Off
o = Outputs On
Q = Pre-existing Output
J'"' = Positive Edge Transition

Block Diagrams
DP7310/DP8310

o--:;::==::f-:~:-l

(0011

DATA (0121
IN 2

O--l~::t=::f-:~:-l

DATA OUT 2
(DDzl

••
•

DATA IN a
(Dial
WRITE

DATA OUT 1

DATA (0111
IN 1

·••

••
•

DATA OUT a
(DDal

o--+-~-Ir-'--l

ENAB~l

(WEl)

WRITE ENAILfJ
(WE21
TLIF15246-3

DP7311/DP8311
DATA (0111
IN 1 :

DATA IN 2
(012)

t

~

,.' CH

"'~JCH

~DATAOUTl

o--~-~--.j....-.r--I_

••
••
•
•
DATA (Dla)
IN a 0--1~::!=::f~:;:-1
••
•

(001)

'::"

DATA OUT 2
(002)

DATA OUT a
(OOa)

CLEAR ~~..I..-"""

(m)
ST.

(STR)~--""'

_ _'"
TLIFI5246-4

5-8

r-----------------------------------------------------------~c

."

Switching Time Waveforms

~

....

o
......

DP7310/DP8310

C
."

....
....
....
......

3V

Co)

DATA INPUT
OV

C

3V

."

WEl OR WE2

Co)

C»

....

o
......

OV - - - - , - - " [ " 1

V+

C

-------"L.

."
C»

....
....

OUTPUT

Co)

VOL
TLlF/5246-5

DP7311/DP8311

3V
DATA INPUT
OV
3V

S'iii"
OV

---t----r---

3V---4-----~-------r--------_;--------~

fIJI
OV
V+
OUTPUT

VOL ---.....TLlF/5246-6

Switching Time Test Circuits
5V

5V

V+ =10V

V+ =10V

Vcc

RL=100Q

RL=100Q

OUT

OUT

!-

CL=50pF

TLlF/5246-7

TLlF/5246-8

'WE1 = OV When Ihelnpul = WE2

Pulse Generalor Characteristics:
Zo = 50n,Ir = I, = 5 ns

FIGURE 1. DP7310/DP8310

FIGURE 2. DP7311/DP8311

5·9

YY-

C")

co

D.

,------------------------------------------------------------------------------------------,

Typical Applications DP8310/11 Buffering High Current Device (Notes 1 and 2)

C

PNP High Current Driver

C;

NPN High Current Driver
30Y MAX.

Y-

Y+

30Y MAX

C")

co

D.

C
......
YY-

C")

r0-

D.

1 OF 8
OUTPUTS

1 OF 8
OUTPUTS

C

c:;

Y-

Y-

C")

s:c

TL/F/5246-10

TUF/5246-9

VMOS High Current Driver

Circuit Used to Reduce Peak
Transient Lamp Current

YG

VB=6.3V
RG

AB

=

(VB ~ VL ) AL

AB

=

63- 1) IBn = 95.4::: loon
(-'-1-

1 OF 8

OUTPUTS

TL/F/5246-11
TL/F/5246-12

Eight Output/Four Output Fiber OptiC LED Driver
DP8311100 mA Drivers

DP8311 Parallel Outputs (200 mAl Drivers'
Y+

Y+
l00mA I
MAX. t
1 OF 8
OUTPUTS
FALLTHROUGH

200mA I
MAX. t

Ro

RD

~LEDTO
~LEDTO

1 DF4

ABER OPTIC

RBER OPTIC

OUTPUTS
FALLTHROUBH

MODE

MODE

TUF/5246-13

'Parallel only adjacent outputs
TUF/5246-14

5-10

c

Typical Applications

~
.....

(Continued)

8-Blt Level Translator-Driver
V+

+5

LOAD OR
OUTPUT PULL·UP

INPUT

Vee

,-30V

ISIN

1.4VIh-b ov

BOUT

I

C

....

."

Vour

r~i~

.....

Co,)

.....
......
C

."
CO

g(~~"""'-~--1
T

---1---ov

0P8311
+5

~

Digital Controlled 256 Level
Power Supply from 1.2V to 30V

.....

Co,)

(:)
......

A

CUi

C

."
CO

.....
.....

Co,)

TL/F/5246-15

'SETS VOUT

TLlF/5246-16

200 mA Drive for a 4 Phase Blfllar Stepper Motor

Reading the State of the Latched Peripherals
V+

+VSTEPPER

30V MAX.

U
S

DATA BUS

A
T

Y 1--::--'" I A

S
T
E
M

UPS310

S
y
S '""'""......-1
T
E

ADDRESS/CE

'Parallel only
adJaeenl oulpuls

M

'High Levellnpul
Yoltage must nol
Exceed Yee of Ihe
DM81LS96

TL/F/6246-17

TL/F/6246-16

Nole I: Always use good Yee bypass and ground leehnlqueslo suppress Iranslenls caused by peripheral loads.
Nole 2: Prinled circuit board mounting is required If Ihese devices are operaled al maximum rated lemperalure and current (all outpuls on DC).

5-11

~
CO)

CD

r------------------------------------------------------------------------------------,

~National

~ ~ Semiconductor
.....
CO)
CO)

CD

~

OS1631/0S3631/0S1632/0S3632/0S1633/0S36331

C
.....
OS1634/0S3634 CMOS Oual Peripheral Orivers
N
CO)
CD

~

C
.....
....
CO)

CD

~
.....
....
~
CO)

CD

~
.....
CO)
CO)

....
CD

~

~
CO)

CD
....
~
.....
....
CD
....
CO)

General Description
The DS1631 series of dual peripheral drivers was designed
to be a universal set of interlace components for CMOS
circuits.
Each circuit has CMOS compatible inputs with thresholds
that track as a function of Vee (approximately Yo Vee). The
inputs are PNPs providing the high impedance necessary
for interlacing with CMOS.

dance OFF state with the same breakdown levels as when
Vee was applied .

Outputs have high voltage capability, minimum breakdown
voltage is 56V at 250 /LA.
The outputs are Darlington connected transistors. This allows high current operation (300 mA max) at low internal
Vee current levels since base drive for the output transistor
is obtained from the load in proportion to the required loading conditions. This is essential in order to minimize loading
on the CMOS logic supply.

The DS1631 series is also TIL compatible at Vee = 5V.

Pin-outs are the same as the respective logic functions
found in the following popular series of circuits: DS75451,
DS75461. This feature allows direct conversion of present
systems to the MM74C CMOS family and DS1631 series
circuits with great power savings.

Features
•
•
•
•
•

CMOS compatible inputs
High impedance inputs
PNP's
High output voltage breakdown
56V min
High output current capability
300 mA max
Same pin-outs and logic functions as DS75451 and
DS75461 series circuits
• Low Vee power dissipation (28 mW both outputs "ON"
at 5V)

Typical Vee = 5V power is 28 mW with both outputs ON.
Vee operating range is 4.5V to 15V.
The circuit also features output transistor protection if the
Vee supply is lost by forcing the output into the high impe-

~ Connection Diagrams (Dual-In-Line and Metal Can Packages)
Vee

82

AI

AI

81

XI

X2

Vee

BZ

A2

X2

Vc:c

GND

TLlF/5816-1

Top View
Order Number DS1631J·8
or DS3631N
v~

BZ

A2

AlII

XI

TLlF/5816-2

Xl

Vee

IZ

A2

GND

AI

81

XI

Top View

Top View

UID

TL/F/5818-4

TL/F/5818-3

Order Number DS1632J·8
Order Number DS1633J-8
or DS3632N
or DS3633N
See NS Package Number J08A or N08E

xz

Top View
Order Number DS1634J-8
orDS3634N

v~

GND

GN.

GND

GN.

TLlF/5816-5

TLlF/5816-6

TL/F/5816-7

TL/F/5816-8

Top View

Top View

Top View

Top View

(Pin 4 is electrically connected to the

(Pin 4 is electrically connected to the
case.)

(Pin 4 is electrically connected to the
case.)

(Pin 4 is electrically connected to the
case.)

case.)

Order Number DS1631H

Order Number DS1632H
Order Number DS1633H
See NS Package Number H08C
5-12

Order Number DS1634H

Absolute Maximum Ratings (Note 1)

Operating Conditions

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Oistributors for availability and specifications.
5upply Voltage

5upply Voltage, Vee
051631/0516321
0516331051634

16V

Voltage at Inputs

- 65'C to + 150'C

083631/0536321
0536331053634

1133mW
1022mW
787mW

Temperature, TA
051631/0516321
051633/051634

Lead Temperature (50ldering, 4 sec.
260'C
'Derate cavity package 7.6 mWl"e above 2S'C; derate molded package
8.2 mWI'e above 2S'e; derate TO-S package S.2 mWI"e above 2S'C.

053631/0536321
0536331053634

56V

5torage Temperature Range
Maximum Power Oissipation" at 25'C
Cavity Package
Molded Package
TO-5 Package

Electrical Characteristics

I

Parameter

Max

Units

4.5

15

V

4.75

15

V

-55

+125

'C

0

+70

'C

-0.3V to Vee + 0.3V

Output Voltage

Symbol

Min

(Notes 2 and 3)

I

I Min I Typ I Max IUnits

Conditions

ALL CIRCUITS
VIH

VIL

Logical "1" Input Voltage

Logical "0" Input Voltage

(Figure 1)

(Figure 1)

Vee = 5V

3.5

2.5

V

Vee = 10V

8.0

5

V

Vee = 15V

12.5

7.5

V

Vee = 5V

2.5

1.5

Vee = 10V

5.5

2.0

V

Vee = 15V

7.5

2.5

V

V

IIH

Logical "1" Input Current

Vee = 15V, VIN = 15V, (Figure2)

0.1

10

p.A

IlL

Logical "0" Input Current

VIN = O.4V, (Figure 3)

Vee = 5V

-50

-120

p.A

Vee = 15V

-200

-360

p.A

VOH

Output Breakdown Voltage Vee = 15V,IOH = 250 p.A, (Figure 1)

VOL

Output Low Voltage

56

65

V

Vee = Min, (Figure 1),
051631,051632,
IOL = 100 mA
051633,051634
IOL = 300mA

0.85

1.1

V

1.1

1.4

V

Vee = Min, (Figure 1),
053631, 053632,
053633, 053634

IOL = 100 mA

0.85

1.0

V

IOL = 300 mA

1.1

1.3

V

VIN = OV, (Figure 4)

Vee = 5V

Output Low

7

11

mA

Vee = 15V

Both Orivers

14

20

mA

Vee = 5V, VIN = 5V

Output High

2

3

mA

7.5

10

mA

0516311053631
lee(o)

5upply Currents

(Figure 4)

lee(l)

Vee = 15V, VIN = 15V Both Orivers
tpol

Propagation to "1"

Vee = 5V, TA = 25'C, CL = 15 pF, RL = 500, VL = 10V,
(Figure 5)

500

ns

tpDO

Propagation to "0"

Vee = 5V, TA = 25'C, CL = 15 pF, RL = 500, VL = 10V,
(Figure 5)

750

ns

051632/053632
ICC(O)

5upply Currents

(Figure 4)

Vee = 5V, VIN = 5V

Output Low

Vee = l5V, VIN = 15V
VIN = OV, (Figure 4)

lee(l)

Vee = 5V

Output High

Vee = 15V

8

12

mA

18

23

mA

2.5

3.5

mA

9

14

mA

tpol

Propagation to "1"

Vee = 5V, TA = 25'C, CL = 15 pF, RL = 500, VL = 10V,
(Figure 5)

500

ns

tpoo

Propagation to "0"

Vee = 5V, TA = 25'C, CL = 15 pF, RL = 500, VL = 10V,
(Figure 5)

750

ns

5-13

Electrical Characteristics (Notes 2 and 3) (Continued)
Symbol

I

Parameter

OS1633/0S3633
lee(o)

Supply Currents

I

I Min I Typ I Max I Units

Conditions
VIN = OV, (Figure 4)

Output Low

Vee = 5V
Vee = 15V

(Figure 4)

Ice(1)

Vee = 5V, VIN = SV

Output High

Vce = 15V, VIN = 15V

7.5

12

16

23

rnA
rnA

2

4

rnA

7.2

15

rnA

tp01

Propagation to "1"

Vce = 5V, TA = 25'C, CL = 15 pF, RL = 500., VL = 10V,
(FigureS)

500

ns

tpoo

Propagation to "0"

Vce = 5V, TA = 2S'C, CL = 15pF, RL = 500., VL = 10V,
(FigureS)

7S0

ns

(Figure 4)

7.5

12

18

23

081634/0S3634
lce(o)

Supply Currents

Vee = SV, VIN = 5V

Output Low

Vee = 15V, VIN = 15V
VIN = OV, (Figure 4)

Ice(1)

Output High

Vce = SV
Vee = 1SV

tp01

Propagation to "1 "

Vee = 5V, TA = 2S'C, CL = 15 pF, RL =
(FigureS)

son, VL =

10V,

3

5

11

18

500

rnA
rnA
rnA
rnA
ns

Vee = 5V, TA = 2S'C, CL = 15 pF, RL = son, VL = 10V,
ns
750
(FigureS)
Note 1: "Absolute Maximum Ratings" are those values beyond which the safely of the device cannot be guaranteed. Except for "Operating Temperature Range"
they are not meant to Imply that the devices should be operated attheso limits. The table of "ElectMcal Characterlsllcs" provides conditions for actual device

tpDO

Propagation to "0"

operation.

Note 2: Unless otherwise specKled minImax limits apply across the -55'C to +125"C temperature range for the 081631, 081632, 081633 and 081634 and
across the O'C to +70'C range for the 083631. 083632, 083633 and 083634. All typical values are for TA = 25'C.
Note 3: All currents Into device pins shown as positive, out of device pins as negative, all vollages referenced to ground unless otherwise noted. All values shown
as max or min on absolute value basis.

Test Circuits

v~

L~
V'Ho-V'L 0--

r-...

-~
SEE
TEST
TABLE

B

_~

r
CIRCUIT
UNDER
TEST

Y
-

~~

SEE
TEST
....TABLE

VOH

~IOL

VOL

!~

~

~

Output

Input
Under
Test

Other
Input

Apply

Measure

083631

VIH
VIL

VIH
Vee

IOH
IOL

VOH
VOL

083632

VIH
VIL

VIH
Vce

IOL
IOH

VOL
VOH

083633

VIH
VIL

GNO

IOH
IOL

VOH
VOL

VIH
VIL

GNO

IOL
IOH

VOL
VOH

Circuit

053634

VIL
VIL

Note: Each Input Is tested separately.
FIGURE 1. VIH, VIL, VOH, VOL

5-14

TL/F/5818-9

~
....
en
....
.....
C
....
en

Test Circuits (Continued)

Co)

U)
Co)

N
.....

C

....
en

U)
Co)

~

TLlF/5816-10

~
....

Each input is tested separately.

en
Co)

FIGURE 2.IIH

.a:o.
.....
C

U)

Vee

J
r-u'--- 1

Vee

ICCH
y
V,L

~B.A

j?~

Co)

en
Co)

OPEN

~A

en

I

~~B

o-----"1L.....,..---1

....
.....
~
Co)

OPE
:

ICCL

Co)

I

N
.....

I

I

L-----I'

~

Co)

en

Co)

':' GNO
TL/F/5816-12

Both gates are tested simultaneously.
TL/F/5816-11

FIGURE 4. Icc for AND and NAND Circuits

Note A: Each Input is tested separately.

~
~

Co)

.a:o.

Note B: When testing 051633 and 051634 input not under test is grounded.
For all other circuits it is at Vee-

FIGURE 3. IlL

Schematic Diagram (Equivalent Circuit)
r----t~------------~.---_t~~Vee

INPUT

OUTPUT

I

~

LOGIC
AND LEVEL
TRANSLATION
ELEMENTS

I

L __ ..J

lIZ of circuit shown

GND
TL/F/5816-15

5·15

~
C")

CD

C")

~
......

r---------------------------------------------------------------------------------,
Switching Time Waveforms

C")
C")

5.0V

INPUT

IOV

~

~

~
.....

Q
>.~

053631,
053632

C\I

C")

~

I

~
.....
....

"'-,,---4:)

I

PUL5E
GENERATOR
(NOTE 1)

C")

~

~
.....

RL = 50

I--

CIRCUIT
UNDER
TE5T

OUTPUT

x

' - - - - - r - - -.......
GNo

~
C")

053633,
053634

I

CD

I

~
.....

~

....

C")
C")

-~

OV

....

CD

TUF/5816-13

(/)

c

(;j
C")

CD
....

~
.....

....

C")

CD
....

~

S.OV
INPUT
OSI631
oSI633
DV----~~~------------------------~

i---------------D.5ps-----------i
~5.Dn.

5.DV---+-I-l.~~-----------_:::::::"\I
INPUT
051632
051634

DV
VOH

------::::::"\1

IID%

OUTPUT

VOL------~-~~-----------------------------'I
TLlF/5816-14

Note 1: The pulse generator has the following characteristics: PRR

= 500 kHz, loUT::::

50n

Note 2: CL includes probe and jig capaCitance

FIGURE 5. Switching Times

5-16

.------------------------------------------------------------------,0
en
N

~National

o

o

.....
......
oen
CD

~ Semiconductor

0)
0)

052001/059665/052002/059666
052003/059667/052004/059668

UI
......
oen
N

High Current/Voltage Oarlington Drivers

o
o

N

General Description
The OS2001/0S9665/0S2002/0S9666/0S2003/0S9667
OS2004/0S9668 are comprised of seven high voltage, high
current NPN Oarlington transistor pairs. All units feature
common emitter, open collector outputs. To maximize their
effectiveness, these units contain suppression diodes for
inductive loads and appropriate emitter base resistors for
leakage.
The OS2001 IOS9665 is a general purpose array which may
be used with OTL, TTL, PMOS, CMOS, etc. Input current
limiting is done by connecting an appropriate discrete resistor to each input.

The OS2004/0S9668 has an appropriate input resistor to
allow direct operation from CMOS or PMOS outputs operating from supply voltages of 6.0V to 15V.

The OS2002/0S9666 version does away with the need for
any external discrete resistors, since each unit has a resistor and a Zener diode in series with the input. The OS20021
OS9666 was specifically designed for direct interface from
PMOS logic (operating at supply voltages from 14V to 25V)
to solenoids or relays.

II Seven high gain Oarlington pairs

The OS2003/0S9667 has a series base resistor to each
Oarlington pair, thus allowing operation direclly with TTL or
CMOS operating at supply voltages of 5.0V.

Connection Diagram

The OS2001/0S9665/0S2002/0S9666/0S2003/0S9667
OS2004/0S9668 offer solutions to a great many interface
needs, including solenoids, relays, lamps, small motors, and
LEOs. Applications requiring sink currents beyond the capability of a single output may be accommodated by paralleling the outputs.

IN A
IN B
IN C
IN D
IN E
IN F
IN G

'-'

2

16

3

~

14

4

~

13

5

~

12

6

~

11

~

10

I

9

GND-l

h.-

......

o

~

o
o
(0)

......

o

~

.....
......
o

~

• High output voltage (VCE = 50V)
• High output current (Ic = 350 mAl
III OTL, TTL, PMOS, CMOS compatible
iii Suppression diodes for inductive loads
t!I Extended temperature range

o
o.jlo.

......

o

~

0)
0)
0)

Order Numbers

15

7

0)
0)
0)

0)
0)

features

16-LeadDIP
1

......
oen
CD

JPackage
Number
J16A

N Package
Number
N16E

M Package
Number
M16A

OS2001
OS9665

OS2001MJ
OS2001TJ
OS2001CJ
OS9665MJ
OS9665TJ
OS9665CJ

OS2001TN
OS2001CN
OS9665TN
OS9665CN

OS200HM
OS2001CM

OS2002
OS9666

OS2002MJ
OS2002TJ
OS2002CJ
OS9666MJ
OS9666TJ
OS9666CJ

OS2002TN
OS2002CN
OS9666TN
OS9666CN

OS2002TM
OS2002CM

OS2003
OS9667

OS2003MJ
OS2003TJ
OS2003CJ
OS9667MJ
OS9667TJ
OS9667CJ

OS2003TN
OS2003CN
OS9667TN
DS9667CN

D52003TM
DS2003CM

OS2004
OS9668

OS2004MJ
OS2004TJ
OS2004CJ
OS9668MJ
OS9668TJ
OS9668CJ

DS2004TN
DS2004CN
OS9668TN
OS9668CN

OS2004TM
OS2004CM

OUT A
OUT B
OUT C
OUT D
OUTE
OUTF
OUT G
COtoltolON
TLIF19647-1

Top View

5-17

•

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
5torage Temperature Range
CeramicOIP
-6S'Cto + 17S'C
Molded OIP
-6S'C to + lS0'C
Operating Temperature Range
052001M/05966SM
-SS'C to + 12S'C
052002M/059666M
- SS'C to + 12S'C
052003M/059667M
- SS'C to + 12S'C
052004M/059668M
- SS'C to + 12S'C
052001T/05966ST
- 40'C to + 10S'C
052002T/059666T
- 40'C to + 10S'C
052003T1059667T
-40'C to + 10S'C
052004T1059668T
- 40'C to + 10S'C

052001 C/05966SC
052002C/059666C
052003C/059667C
052004C/059668C

O'Cto
O'Cto
O"Cto
O"Cto

+8S'C
+8S'C
+8S'C
+8S'C

Lead Temperature
Ceramic DIP (50Idering. 60 seconds)
300'C
Molded OIP (50Idering. 10 seconds)
26S'C
Maximum Power Dissipation' at 2S'C
Cavity Package
2016mW
Molded Package
1838mW
5,0. Package
926mW
'Derate cavity package 16.13 mWI"C above 25'C; derate molded DIP package 14.7 mWI'C above 25"C. Derate S.O. package 7.4 mW/'C.
Input Voltage
30V
SSV
Output Voltage
Emitter-Base Voltage
Continuous Collector Current

6.0V
SOOmA
2SmA

Continuous Base Current

Electrical Characteristics TA = 2S'C. unless otherwise specified (Note 2)
Symbol

Parameter

ICEX

Output Leakage
Current

Conditions

II(ON)

Collector-Emitter
5aturation Voltage

Input Current

II(OFF)

Input Current
(Note 4)

VI(ON)

Input Voltage
(NoteS)

hFE

OC Forward Current
Transfer Ratio

Typ

=
=

Max

Units

100

= 6.0V (Figure 1b)
052002/059666
052004/059668
VCE
SOV. VI = 1.0V (Figure 1b)
Ic = 3S0 mAo 18 = SOO p.A (Figure 2) (Note 3)
Ic = 200 mAo 18 = 3S0 p.A (Figure 2)
IC = 100 mAo 18 = 2S0 p.A (Figure 2)
VI = 17V (Figure 3)
052002/059666
VI = 3.8SV (Figure 3)
052003/059667
052004/059668
VI = S.OV (Figure 3)
VI = 12V (Agure 3)
TA = 8S'C for Commercial
Ic = SOO p.A (Figure 4)
VCE = 2.0V.lc = 300 mA (Figure 5)
052002/059666
052003/059667
VCE = 2.0V. Ic = 200 mA (Figure 5)
VCE = 2.0V. Ic = 2S0 mA (Figure 5)
VCE = 2.0V. Ic = 300 mA (Figure 5)
052004/059668
VCE = 2.0V.lc = 12S mA (Figure 5)
VCE = 2.0V.lc = 200 mA (Figure 5)
VCE = 2.0V. Ic = 27S rnA (Figure 5)
VCE = 2.0V.lc = 3S0rnA(Figure5)
052001/05966S
VCE = 2.0V. Ic = 3S0 rnA (Figure 2)
VCE

VCE(Sat)

Min

TA = 8S'C for Commercial
VCE = SOV (Figure 1a)

p.A

SOV, VI

SOO
SOO
1.2S

SO

1.6

1.1

1.3

0.9

1.1

0.8S

1.3

0.93

1.3S

0.3S

O.S

1.0

1.4S

V

mA

p.A

100
13
2.4
2.7
3.0

V

S.O
6.0
7.0
8.0
1000

CI

Input Capacitance

30

pF

tpLH

Turn-On Delay

O.S VI to O.S Vo

lS

1.0

p's

tpHL

Turn-Off Oelay

O.S VI to O.S Vo

1.0

p.s

IR

ClampOiode
Leakage Current

VR

SO
100

p.A
p.A

=

SOV (Figure 6)

TA
TA

=
=

2S'C
8S'C

ClampOiode
IF = 3S0 mA (Figure 7)
1.7
2.0
V
Forward Voltage
Note 1: "Absolute Maximum Ratings" are those values beyond which the safety of the device cannot be guaranteed. They are not meant to Imply that the devices
should be operated atthesa limits. The tables of "Electrical Characteristics" provida conditions for actual device operation.
Note 2: All limits apply to the complete Da~ington series except as specified for a single device type.
Note 3: Under normal operating conditions thesa units will sustain 350 rnA per oulputwith VCE (Sat) = 1.eV at 70'Cwith a pulsawidth of 20 ms and a duty cycle of
30%.
Note 4: The II(OFF) current limit guaranteed against partial turn-on of the output.
NDte 5: The VI(ON) voltage limit guarantees a minimum output sink current par the specified test conditions.

VF

S-18

Typical Performance Characteristics
Collector Current vs
Saturation Voltage
800

,

.coo

hplC~_-, -

,

I

I

",

~ ft'
" /
II

o
o

o.s

MAX/

,

/

V

"

/
D

o

1.5

200

SAWRATION VOLTAGE - V

§

1.0

o

, V
,/

LIMIT

1.5

o

40D

,

TYP

V
~
=
0.5

L

/

MA}

1

,

,

V

1.0

2.D

TYPICAL,

(2 PARALLELED DEVICES) ' "

TYPICAl
(SINGLE DEVICE)

OS2002/0S9666
Input Current vs
Input Voltage

Collector Current vs
Input Current

12

SOD

INPUT CURRENT - i'A

,

", ,
14

16

18

,,

,

.'

2D

22

24

26

INPUT VOLTAGE - V
TL/F/9647-6

OS2003/0S9667
Input Current vs
Input Voltage

r ,

2.5

,

2.D

IS

1.5

~
~

2.D

...

/

/

1.0

,.

,'

o

i

,

D

2.D 3.0

<1J)

,

§

(,

= 0.5

1

1.5

'"

,. V
/'

~

0.5

~

8

~

TYP

~

~

~~

~

~

5.0 8.D 7.0 8.D 9.0

INPUT VOLTAGE - V

2DO

~

~

o

5.0 6.D 7.0 8.D 9.0

o 300

. /V
MAX ,/"

1.0

2

~

MAX/TYP,

1
-

Peak Collector Current vs
Outy Cycle and Number of
1 Outputs (Molded Package)
,4OD'-'OT"-.---.--r--v;....,......,,......,

OS2004/0S9668
Input Current vs
Input Voltage

10

11

12

INPUT VOLTAGE - V

~

100
2D

40

60

80

100

DUTY CYCLE - "
TL/F/9647-'8

Peak Collector Current vs
Outy Cycle and Number of
Outputs (Ceramic Package)

!

300

f--4\MtHr-+*--t---l

8

'"i:5

7

... 200 NUMBER ~'I<'\,,-.30<-~f-...3I,j
~
OF OUTPUTS
lI'
CONDucnNG
~
SIMULTANEOUSLY
100 TA = 70·C

o

20

40

60

BO

100

DUTY CYCLE - "
TL/F/9647-'9

•
5·19

co
CD

I..

r-------------------------------------------------------------------------------------,
Equivalent Circuits

......

r-IM-- COMMON

0$2001/0$9665

CI
CI
N

r---~H""'-- OUT

2.7k.o.

IN-..---1

~

..........-COMMON

0$2003/0$9667

~---1~~---0~

IN --'lM......---1

~
CD

~......

7.2k.o.

3.0k.o.

i~

......

COMMON

~

I

TLlF/9647-3

TUF/9647-2

10.5k.o.
IN -

...-

~~--COMt.tON

0$2004/0$9668

r - - -...........- - - OUT
.........""'......- - \

r----~

__

---OUT

IN --'lM......---1

......
N

I

~
......

TL/F/9647-4

Il)

~

~......
....

TUF/9B47-5

Test Circuits

I

OPEN +50V

OPEN +50V

OPEN

OPEN

TUF/9647-7

TUF/9647-B

FIGURE 18

FIGURE 1b

TLlF/9B47-9

FIGURE 2
OPEN

OPEN +50V

OPEN

OPEN

VI.l
TUF/9647-11

TL/F/9647-10

TL/F/9647-12

FIGURE 4

FIGURE 3

FIGURE 5
+50V

OPEN

OPEN
TLlF/9647-14

FIGURE 7
TUF/9647-13

FIGURES
5-20

Typical Applications
PMOS to Load

Buffer for Higher Current Loads
Vz

VI

Vz

VI
16
15
14
DS2003/
DS9667

ll-----l

13
12
11
10

PMOS
OUTPUT

9

m

to load

Vz

VI

TUF/9847-17

5-21

~National

~ Semiconductor

DS3654 Printer Solenoid Driver
General Description
The 083654 is a serial-to-parallel 10-bit shift register with a
clock and data input, a data output from the tenth bit, and
10 open-collector clamped relay driver outputs suitable for
driving printer solenoids.
Timing for the circuit is shown in Figure 1. Data input is
sampled on the positive clock edge. Data output changes

on the negative clock edge, and is always active. Enable
transfers data from the shift register to the open-collector
outputs. Internal circuitry inhibits output enable for power
supply voltage less than 6V.
Each output sinks 250 mA and is internally clamped to
ground at 50V to dissipate energy stored in inductive loads.

Connection Diagram
Pin Descriptions

Dual-In-Llne Package

Pin No.

Function

OUTPUT 8

1
2
3
4
5

OUTPUTS

6

OUTPUT 10

7
8

Output Enable
Output 6
Output 7
Output 8
Output 9
Output 10
Data Output
Ground
Clock Input
Data Input
Output 1
Output 2
Output 3
Output 4
Output 5

OUTPUT ENABLE
OUTPUT 6
OUTPUT7

9

OATAOUTPUT

10
11
12
13
14
15
16

GNO

TL/F/6817-1

Top View
Order Number DS3654N
See NS Package Number N16E

Vee

Logic Diagram
.

OUTPUTS
OUTPUT
ENABLE

I

CLOCK
INPUT

18

vccOe
GNO~
TLlF/5817-2

5-22

Absolute Maximum Ratings

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage, Vee
9.5VMax
Input Voltage
-0.5V Min. 9.5V Max
Output Supply, Vp-p
45V Max
Storage Temperature Range
-65"Cto + 150"C
Output Current (Single Output)
O.4A
Ground Current
4.0A
Peak Power Dissipation t < 10 ms,
Duty Cycle < 5%
4.5WMax

Maximum Power Dissipation" at 25"C
Molded Package
Lead Temperature (Soldering, 4 seconds)
·Derate molded package 13.5 mwrc above 2SoC.

1687 mW
260"C

Operating Conditions
Min
7.5

Supply Voltage (Vccl
Temperature (TAl
Output Supply (Vp-p)

a

Max
9.5
+70
40

Units
V
"C
V

Electrical Characteristics (Notes 2, 3 and 4) Vp-p = 30V unless otherwise noted
Parameter

Conditions

Logical "1" Input Voltage

Min

Typ

= 0.1A, VEN = OV
= 40V, VEN = OV
IOl = 250 mA, VEN = 2.6V

45

Logical "1" Input Current
Clock
Enable
Data
Clock
Enable
Data

TA =
TA =
TA =
TA =
TA =
TA =

0.2
0.2
0.3

Logical "0" Input Current
Clock
Enable
Data

TA
TA
TA

Input Pull-Down Resistance
Clock
Enable
Data

TA = 25"C, VCl < VCC
TA = 25"C, VEN < VCC
TA = 25'C, Vo < VCC

Logical "1" Output Current
Logical

"a" Output Voltage

Supply Current (lee)
Outputs Disabled
Outputs Enabled
Data Output Low (Voou
Data Output High (VOOH)

Units

0.8

V

2.6

V

Logical "a" Input Voltage
Logical "1" Output Voltage Clamp

Max

ICLAMP

50

VOH

70"C, VCl = 2.6V
70"C, VEN = 2.6V
70"C, Vo = 2.6V
O"C, VCl = 2.6V
O"C, VEN = 2.6V
O"C, Vo = 2.6V

= 70"C, VCl = IV
= 70'C, VEN = IV
= 70"C, Vo = 1V

TA ~ 25"C, VEN
VCC = 9.5V
TA ~ 25"C, VEN
Each Bit

0.33
0.33
0.57
0.33
0.33
0.57

65

V

1.0

mA

1.6

V

0~5

0.5
0.75

mA
mA
mA
mA
mA
mA

125
125
220

",A
",A
",A

8
8
4.5

kn
kn
kn

= OV, VOO = OV,

27

40

mA

= 2.6V, IOl = 250 mA

55

70

mA

0.01

0.5

V

= OV, IOl = OV
Vo = 2.6V, IOH = -0.75 mA
Vo = OV, Voo = 1V
Vo

2.6

3.4

V

' 14

kn
They are not meant to imply that the devices
should be operated at these limits. The tebles of "Electrical Characteristics" provide conditions for actual device operation,
Note 2: Unless otherwise specified, minimax limits apply across the O'C to + 70'C temperature range and the 7,5V to 9.5V power supply range, All typical values
given are for Vce = B.SV and TA = 2S'C.
Data Output Pull-Down Resistance

Nole 1: "Absolute Maximum Ratings" are those values beyond which the safety of the device cannot be guaranteed,

Note 3:: All currents into device pins are positive; all currents out of device pins are negative. All voltages are referenced to ground unless otherwise specified.

NOle

4: Only one output at a time should be shorted.

5-23

III

Switching Characteristics (JOC to + 7(JOC, TA =
Parameter

25°C, nominal power supplies unless otherwise noted

Conditions

Typ

Min

Max

Units

2.0
2.0

IJoS

(Figure 1)

Clk, Data and Enable Inputs
tFC

tBIT ~ 10 /Jos

lAc

2
3.5

teLK
teLK
tHOLO
tsET.UP
tRE,tROIN
tFE, tFOIN

1.0
1.0
1.0
5.0

Output 1-10

Vp·p = 20V
RL = 1000, CL
RL = 1000, CL

tRO
tFO
tpOEH
tpOEL
Data Output
tpOH, tpOL
tRO
tFO

< 100 pF
< 100 pF

1.2
1.2
3.5
3.0

/Jos
/Jos
/JoB
/Jos

IJoS
/Jos
/JoS
/JoB

/JoB
/JoB

0.8
0.4
0.4

RL=5kO,CL:S:10pF

/JoS

2.5

IJoS
/JoB
/Jos

Clock to Enable Delay
teE

2tBIT

/Jos

tBIT

/JoB

Enable to Clock Delay

Switching Time Waveforms
r--tEClK-

;--tclK EN--j

OUTPUT
ENABLE
\--tBITMIN

n

CLOCK

tBIT---\

ClK 1

-

V CLOCK

tBIT

-- 2 tBIT MIN--I

rL-cO--

~~~

tRC-

-

IClK

tFC--i- tClK

OATAIN~

I_~

t
-

OUTPUT
ENABLE

OUTPUT

]f'"

i-tHOlD
tSET-UP

~]

I---tRD tFD-l

'~1

~~
-I

!-tFO

-

CLOCK

DATA OUT

J

J{~.

\
!-tPOl

FIGURE 1. ShIft TimIng

5·24

tRO

\:

X

--I

\-tRD tFO
TUF/58t7-3

Definition of Terms
vp-p: Output power supply voltage. The return for open-col-

tCLK: The portion of tSIT when VCLK ,;: O.BV

lector relay driver outputs.

tSET-UP: The time prior to the end of tcLK required 10 insure
valid data at the shift register inpul for subsequent clock
transitions.

tSIT: Period of the incoming clock.
VCLK: The voltage at the clock input.

'eLK: The portion of tSIT when VCLK ;;, 2.6V

tHOLO: The time following the start of tcLK required to transfer data within the shift register.

II

5-25

G)
In
CD

C")

~

r-----------------------------------------------------------------------------------~

~National

~ Semiconductor

053658 Quad High Current Peripheral Driver
General Description
The OS3658 quad peripheral driver is designed for those
applications where low operating power, high breakdown
voltage, high output current and low output ON voltage are
required. A unique input circuit combines TTL compatibility
with high impedance. In fact, its extreme low input current
allows it to be driven directly by a CMOS device.
The outputs are capable of sinking 600 mA each and offer a
70V breakdown. However, for inductive loads the output
should be clamped to 35V or less to avoid latch-up during
turn off (inductive fly back protection-refer AN-213). An onchip clamp diode capable of handling 800 mA is provided at
each output for this purpose. In addition, the OS3658 incorporates circuitry that guarantees glitch-free power up or
down operation and a fail-safe feature which puts the output
in a high impedance state when the input is open.

•
•
•
•

The molded package is specifically constructed to allow increased power dissipation over conventional packages. The
four ground pins are directly connected to the device chip
with a special copper lead frame. When the quad driver is
soldered into a PC board, the power rating of the device
improves significantly.

•
•
•
•
•
•
•
•
•
•
•
•

Applications
•
•
•
•
•
•

Relay drivers
Lamp drivers
Solenoid drivers
Hammer drivers
Stepping motor drivers
Triac drivers

Connection Diagram

LED drivers
High current, high voltage drivers
Level translators
Fiber optiC LED drivers

Features
•
•
•
•
iii

Single saturated transistor outputs
Low standby power, 10 mW typical
High impedance TTL compatible inputs
Outputs may be tied together for increased current capacity
High output current
600 mA per output
2.4A per package
No output latch-up at 35V
Low output ON voltage (350 mV typ @ 600 mAl
High breakdown voltage (70V)
Open collector outputs
Output clamp diodes for inductive fly back protection
NPN inputs for minimal input currents (1 /LA typical)
Low operating power
Standard 5V power supply
Power up/down protection
Fail safe operation
2W power package
Pin-for-pin compatible with SN75437

Truth Table

Dual-In-Llne Package
IN A

IN B

EN

GND

GND

Vee

IN C

IN D

IN

EN

OUT

H

H
H

L
Z
Z
Z

L
H
L

DUT A CLAMP 1 DUT B

GND

GND

DUT C CLAMP 2 DUT D
TLlF/5819-1

Top View
Order Number DS3658N
See NS Package Number N16E

5-26

L
L

H

~

High slale

L

~

Low stale

Z

~

High impedance stale

Absolute Maximum Ratings (Note 1)

Operating Conditions

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage
7V
Input Voltage
15V
Output Voltage
70V
Output Current
1.5A
Continuous Power Dissipation
@ 25·C Free·Air (Note 5)
2075mW
Storage Temperature Range
- 65·C to + 150·C
Lead Temperature (Soldering, 4 sec.)
260·C

Min
4.75
0

Supply Voltage
Ambient Temperature

Max
5.25
70

Units
V
·C

Electrical Characteristics (Notes 2 and S)
Symbol

Parameter

Conditions

VIH

Input High Voltage

VIL

Input Low Voltage

IIH

Input High Current

VIN = 5.25V, Vcc = 5.25V

IlL

Input Low Current

VIN = 0.4V

VIK

Input Clamp Voltage

11= -12mA

VOL

Output Low Voltage

IL = SOOmA

Min

Typ

Max

Units

O.B

V

10

IJ.A

±10

IJ.A

-O.B

-1.5

V

0.2

0.4

V

0.S5

0.7

V

100

IJ.A

V

2.0

1.0

IL = 600 mA (Note 4)
ICEX

Output Leakage Current

VCE = 70V, VIN = O.BV

VF

Diode Forward Voltage

IF = BOOmA

IR

Diode Leakage Current

VR = 70V

Icc

Supply Current

All Inputs High
All Inputs Low

1.0

1.6

V

100

IJ.A

60

85

mA

2

4

mA

Switching Characteristics (Note 2)
Symbol
tpHL

Parameter

Conditions

Turn On Delay

RL = 600, VL = SOY

Min

Typ

Max

Units

226

500

ns

Turn Off Delay
24S0
8000
RL = 600, VL = SOy
ns
tpLH
Nole 1: "Absolute Maximum Ratings" are those values beyond which the safety of the device cannot be guaranteed. They are not meant to Imply that the device
should be operated at these limits. The table of "Electrical Characteristics" provides conditions for actual device operetlon.
Nole 2: Unless otherwise specified, minimax limits apply across the O'C to +70'C temperature range and the 4.7SV to S.2SV power supply range. All typical
values are for TA = 25'C and Vee = 5.0V.
Nole 3: All currents into device pins are shown as positive; all currents out of device pins are shown as negative; all voltages are referenced to ground, unless
otherwise specified. All values shown as max or min are so classified on absolute value basis.
Nole 4: All sections of this quad circuit may conduct rated current simultaneously; however, power dissipation averaged over a short Interval of time must fall within
specified continuous dissipation ratings.
Note 6: For operation over 25'C free-air temperature, derate linearly to 1328 mW @ 70'C @ the rate 0116.6 mW/'C.

5·27

AC Test Circuit

Switching Waveforms
Vee

30V

3V

INPIIT

::{.l,5V

OY

6l1li
30Y

OUT

OUTI'I/T

. . .r

YOL

3OpF*

~

~

10%
TLlF/5819-3

TL/F/5819-2

'Includes probe and jig capaci1ance

Typical Applications
Stepping Motor Driver

Lamp Driver

YIIoToII* *

5V

I""

tl1

5V

-

V+

...Jt.
~
1

2
3

~

!J
III

9, 10, 15, 16 ~
:I!
DATA BUS )

......
'",..

'"

!:!

',10,15,16

DS365B

r

CONTROL

L3*

~

L£YELS

D83658

7
14

EN

....

8

L4*

~.

-

14
-+EN

J!,5,12,13

4,5,12,13
TLlF/5819-4

'L I, L2, L3, L4 are the windings of a bifilar stepping motor

TL/F/5819-5

"VMOTOR is the supply voltage of the motor

5·28

~en

~National

en

~ Semiconductor

CD

DS3668 Quad Fault Protected Peripheral Driver
General Description

Applications

The DS3668 quad peripheral driver is designed for those
applications where low operating power, high breakdown
voltage, high output current and low output ON voltage are
required. Unlike most peripheral drivers available, a unique
fault protection circuit is incorporated on each output. When
the load current exceeds 1.0A (approximately) on any output for more than a built-in delay time, nominally 12 P.s, that
output will be shut off by its protection circuitry with no effect
on other outputs. This condition will prevail until that protection circuitry is reset by toggling the corresponding input or
the enable pin low for at least 1.0 ,.,.s. This built-in delay is
provided to ensure that the protection circuitry is not triggered by turn-on surge currents associated with certain
kinds of loads.
The DS3668's inputs combine TIL compatibility with high
input impedance. In fact, its extreme low input current allows it to be driven directly by a MOS device. The outputs
are capable of sinking 600 mA each and offer a 70V breakdown. However, for inductive loads the output should be
clamped to 35V or less to avoid latch up during turn off
(inductive fly-back protection - refer AN-213). An on-Chip
clamp diode capable of handling 800 mA is provided at
each output for this purpose. In addition, the DS3668 incorporates circuitry that guarantees glitch-free power up or
down operation and a fail-safe feature which puts the output
in a high impedance state when the input is open.

•
•
•
•
•
•
•
•
•

The molded package is specifically constructed to allow increased power dissipation over conventional packages. The
four ground pins are directly connected to the device chip
with a special copper lead frame. When the quad driver is
soldered into a PC board, the power rating of the device
improves significantly.

Connection Diagram

Relay drivers
Solenoid drivers
Hammer drivers
Stepping motor drivers
Triac drivers
LED drivers
High current, high voltage drivers
Level translators
Fiber optic LED drivers

Features
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•

Output fault protection
High impedance TIL compatible inputs
High output current-aOO mA per output
No output latCh-up at 35V
Low output ON voltage (550 mV typ @ 600 mAl
High breakdown voltage (70V)
Open collector outputs
Output clamp diodes for inductive fly-back protection
NPN inputs for minimal input currents (1 p.A typical)
Low operating power
Standard 5V power supply
Power up/down protection
Fail-safe operation
2W power package
Pin-for-pin compatible with SN75437

Truth Table

Dual-In-Line Package
INA

INB

EN

GNO

GNO

Vee

INC

INO

IN

EN

OUT

H
L

H
H
L
L

L
Z
Z
Z

H
L

OUT A CLAMP 1 OUT B

GNO

UNO

OUT C CLAMP 2 OUT 0

H

= High state

L

=

Z

= High Impedance stata

Low state

Order Number DS3668N
See NS Package Number N16E

TL/F/5225-1

Top View

5-29

Absolute Maximum Ratings (Note 1)

Operating Conditions

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage
7.0V

Supply Voltage
Ambient Temperature

Input Voltage

15V

Output Voltage

70V

Continuous Power Dissipation
@ 25'C Free-AIr(6)
Storage Temperature Range

Min
4.75
0

Max
5.25
70

Units
V
'C

2075mW
-65'C to

+ 150'C

Lead Temperature (Soldering, 4 seconds)

260

Electrical Characteristics (Notes 2 and 3)
Symbol

Parameter

Conditions

VIH

Input High Voltage

VIL

Input Low Voltage

IIH

Input High Current

VIN = 5.25V, VCC = 5.25V

IlL

Input Low Current

VIN = 0.4V

VIK

Input Clamp Voltage

11= -12mA

VOL

Output Low Voltage

Min

Typ

Max

Units
V

2.0
0.8

V

1.0

20

IIA

±10

/Jo A

-0.8

-1.5

V

IL = 300mA

0.2

0.7

V

IL = 600 mA (Note 4)

0.55

1.5

V

100

/Jo A

1.6

V

ICEX

Output Leakage Current

VF

Diode Forward Voltage

IF = 800 mA

IR

Diode Leakage Current

VR = 70V

Icc

Supply Current

All Inputs High

62

All Inputs Low

20

ITH

Protection Circuit
Threshold Current

VCE = 70V, VIN = 0.6V
1.2

100

/Jo A

80

mA
mA

1

1.4

A

Switching Characteristics (Note 2)
Typ

Max

Units

tpHL

Symbol

Turn On Delay

Parameter

RL = 600, VL = 30V

Conditions

Min

0.3

1.0

/Jos

tpLH

Turn Off Delay

RL = 600, VL = 30V

2

10.0

/JoS

tFZ

Protection Enable Delay
(after Detection of Fault)

6

12

/JoS

Input Low Time for
1.0
/Jos
Protection Circuit Reset
Note 1: "Absolute Maximum Ratings" are those values beyond which the safety of the device cannot be guaranteed. They are not meant to Imply that the device
should be operated at these limits. The table of "Electrical Characteristics" provides conditions for actual device operation.
Nate 2: Unless otherwise specHied, minImax limits apply across the O'C to +70'C temperature range and the 4.75V to 5.25V power supply range. All typical
values are for TA = 25"C and Vee = 5.0V.
Note 3: All currents into device pins are shawn as positive; all currents out of device pins are shown as negative; all voltages are referenced to ground, unless
otherwise specified. All values shown as max or min are so classIfied on absolute value basis.
Nate 4: All sections of this quad circuit may conduct rated current simultaneously; however, power dissipation averaged over a short Interval of time must fall within
specified continuous dissipation ratings.
Note 5: For operation over 25"C free-air temperature, derate linearly to 1328 mW @ 70'C @ the rate of 16.6 mW/"C.
tRL

5-30

AC Test Circuit

Switching Waveforms
Vee

30V
3V

INPUT

d1.5V
OV
30V

OUTPUT

30 pF*

VOL

~

10%
TL/F/5225-3

-=4, 5'12'13J
TL/F/5225-2

'Includes probe and jig capacitance.

Typical Application
Stepping Motor Driver
¥MOTOn**

5V

t11

i"'"

-

.!;!*

1

2

.

'"

~

'"

9, 10, 15, 16
DATA BUS

~

3

....L2*

6

_L3:"

OS366B

r

-

r-7

14

8

...

L4*

r--

EN

-

..c,5,12,13
·L1, L2, L3, L4 are the windings of a bifilar stepping motor.

TLlF/5225-4

"VMOTOR is the supply voltage of the motor.

Protection Circuit Block Diagram
OUTPUT

INPUT

ENABLE

CURRENT
SENSING
CIRCUITRY

TL/F/5225-5

5-31

~National

~ Semiconductor

DS3669 Quad High Current Peripheral Driver
General Description
The OS3669 is a non-inverting quad peripheral driver similar
to the OS3658. These drivers are designed for those applications where low operating power, high breakdown voltage, high output current and low output ON voltage are required. A unique input circuit combines TTL compatibility
with high impedance. In fact, its extreme low input current
allows it to be driven directly by a CMOS device.

• Stepping motor drivers
• Triac drivers
• LED drivers
II High current, high voltage drivers
• Level translators
• Fiber optic LED drivers

The outputs are capable of sinking 600 mA each and offer a
70V breakdown. However, for inductive loads the output
should be clamped to 35V or less to avoid latch-up during
turn off (inductive fly back protection-refer AN-213). An onchip clamp diode capable of handling 800 mA is provided at
each output for this purpose. In addition, the OS3669 incorporates circuitry that guarantees glitch-free power up or
down operation.

• Single saturated transistor outputs
• Low standby power, 10 mW typical
• High impedance TTL compatible inputs
II Outputs may be tied together for increased current
capacity

The molded package is specifically constructed to allow increased power dissipation over conventional packages. The
four ground pins are directly connected to the device chip
with a special copper lead frame. When the quad driver is
soldered into a PC board, the power rating of the device
improves significantly.

Applications
•
•
•
•

Relay drivers
Lamp drivers
Solenoid drivers
Hammer drivers

Connection Diagram

Features

• High output current
600 mA per output
2.4A per package
• No output latch-up at 35V
• Low output ON voltage (350 mV typ @600 mAl
• High breakdown voltage (70V)
• Open collector outputs
• Output clamp diodes for inductive fly back protection
• NPN inputs for minimal input currents (1 p.A typical)
• Low operating power
• Standard 5V power supply
• Power up/down protection
• 2W power package

Truth Table

Dual·ln·Llne Package
INA

INB

EN

GND

GND

Vee

IN C

IN 0

IN

EN

OUT

L
H
L
H

H
H
L
L

L
Z
Z
Z

H=High state
L=Low state
,Z = High impedance state

OUT A CLAMP lOUT B

GNO

GNO

OUT C CLAMP 2 OUT 0
TLfFI5820-1

Top View
Order Number DS3669N
See NS Package Number N16E

5-32

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage
7.0V
Input Voltage
Output Voltage
Output Current
Continuous Power Dissipation
@25·C Free·Air (Note 5)

Storage Temperature Range

-65·C to

+ 150·C
260·C

Lead Temperature (Soldering, 4 seconds)

Operating Conditions

15V
70V
1.5A

Min
4.75
0

Supply Voltage
Ambient Temperature

Max
5.25
70

Units
V
·C

2075mW

Electrical Characteristics (Notes 2 and 3)
Symbol

Parameter

Conditions

Min

VIH

Input High Voltage

VIL

Input Low Voltage

IIH

Input High Current

VIN = 5.25V, Vee = 5.25V

IlL

Input Low Current

VIN = O.4V

VIK

Input Clamp Voltage

VOL

Output Low Voltage

Typ

Max

2.0

Units
V

0.8

V

1.0

10

",A

±10

",A

11= -12mA

-0.8

-1.5

V

IL = 300mA

0.2

0.4

V

IL = 600 mA (Note 4)

0.35

0.7

V

100

",A

ICEX

Output Leakage Current

VF

Diode Forward Voltage

IF = 800 mA

IR

Diode Leakage Current

VR = 70V

lee

Supply Current

All Inputs Low
EN = 2.0V
All Inputs High

Vc = 70V, VIN = 2V,
VEN = 0.8V
1.0

1.6

V

100

",A

60

85

mA

2

4

mA

Switching Characteristics (Note 2)
Symbol

Parameter

Conditions

Typ

Max

Units

tpHL

Turn On Delay

RL = 600., VL = 30V

Min

226

500

ns

tpLH

Turn Off Delay

RL = 600., VL = 30V

2430

8000

ns

Note 1: "Absolute Maximium Ratings" are those values beyond which the safety of the device cannot be guaranteed. They are not meant to imply that the device

should be operated at these limits. The table of "Electrical Characteristics" provides condftions for actual device operation.
Note 2: Unless otherwise specified, minImax Iimfts apply across the O'C to +70'C temperature range and the 4.7SV to S.2SV power supply range. All typical
values are forTA=2S'C and VCC=S.OV.
Note 3: All currents into device pins are shown as positive; all currents out of device pins are shown as negative; all voltages are referenced to ground, unless
otherwise specified. All values shown as max or min are so classified on absolute value basis.
Note 4: All sections of this quad circuit may conduct rated current simultaneously; however, power dissipation averaged over a short interval of time must fall within
specifjed continuous dissipation ratings.

Nole 5: For operation over 2S'C free·air temperature, derate Iineariy to 1328 mW @70"C

5-33

@

the rate of 16.6 mW/·C.

AC Test Circuit

Switching Waveforms
Vee

30V

11

600
30V -+--II"!'~_-+'"
OUTPUT

OUT

VOL

30 pF"

TL/F/S820-3

-:::4, 5,12, 131
TUF/5B20-2

'Includes probe and jig capacitance

Typical Applications
Stepping Motor Driver

Lamp Driver
Y+

5Y

5V

tll

ro-

1

~

-

2
3

...'"=>
~

9, 10, 15, 16
:IE
DATA BUS

~

,.

-

L2"
9,10,15,16
CONTROL
LEVELS

DS3669

La"

083669

~
7

L4"

14

...

EN

~

.J!' 5, 12, 13

4,5,12,13
TL/F/S820-S

TLlF/S820-4

'L 1, L2, L3, L4 are the windings of a bifilar stepping motor.
"VMOTOR is the supply vonage of the motor.

5-34

~National

~ Semiconductor

DS3680 Quad Negative Voltage Relay Driver
General Description
The DS3680 is a quad high voltage negative relay driver
designed to operate over wide ranges of supply voltage,
common-mode voltage, and ambient temperature, with
50 mA sink capability. These drivers are intended for switching the ground end of loads which are directly connected to
the negative supply, such as in telephone relay systems.
Since there may be considerable noise and IR drop between logic ground and negative supply ground In many applications, these drivers are designed to operate with a high
common-mode range (± 20V referenced to negative supply
ground). Each driver has a common-mode range separate
from the other drivers in the package, which pemits input
signals from more than one element of the system.
With low differential input current requirements (typically
100 poA), these drivers are compatible with TIL, LS and
CMOS logic. Differential inputs permit either Inverting or
non-inverting operation.

The driver outputs incorporate transient suppression clamp
networks, which eliminate the need for external networks
when used in applications of switching inductive loads. A
fail-safe feature is incorporated to insure that, if the + IN
input or both inputs are open, the driver will be OFF.

Features
•
•
•
•
•
•
•

Connection Diagram

-10V to - 60V operation
Quad 50 mA sink capability
TILILS/COMS or voltage comparator input
High input common-mode voltage range
Very low input current
Fail-safe disconnect feature
Built-in output clamp diode

Logic Diagram

Dual-In-Llne Package

+AIN~

~GND
~OUTA
~OUTB

-A IN....!
-B IN..2.

+B IN-±

rll-OUT C
rlLOUT D

+c IN..J.

-c IN--!

t-!!-VEE-

r!-+D IN

-D IN..2.

TLlF/5821-1

Top View
Order Number DS3680J, DS3680M or DS3680N
See NS Package Number J14A, M14A, N14A

TLlF/5821-2

Truth Table
Differential Inputs

Outputs
On

VIO

s: 0.8V

Off

Open

Off

5-35

II

Absolute Maximum Ratings (Note 1)

Recommended Operating
Conditions

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
-70V
Supply Voltage (GND to VEE-, and Any Pin)
Positive Input Voltage (Input to GND)
20V
Negative Input Voltage (Input to VEE-)
-5V
Differential Voltage ( + IN to -IN)
±20V
Inductive Load
LLS:5h

Supply Voltage (GND to VEE -)
Input Voltage (Input to GND)
LogiC ON Voltage (+ IN)
Referenced to -IN
Logic OFF Voltage (+ IN)
Referenced to -IN
Temperature Range

ILS:50 rnA
-100mA

Min
-10
-20

Max
-60
20

Units
V
V

2

20

V

-20
-25

0.8
+85

V
'C

Output Current
Storage Temperature
- 65'C to + 150'C
Maximum Power Dissipation' at 25'C
Cavity Package
1433 mW
Molded Dip Package
1398mW
SO Package
1002 mW
Lead Temperature (Soldering, 4 seconds)
260'C
• Derate cavity package 9.6 mWrc above 2S'C; derate molded dip package 11.2 mWrC above 2S'C; derate SO package 8.02 mW/'C above
2S'C.

Electrical Characteristics (Notes 2 and 3)
Symbol

Parameter

VIH

Logic "1" Input Voltage

VIL

Logic "0" Input Voltage

IINH

Logic "1" Input Current

IINL

Logic "0" Input Current

VOL

Output ON Voltage

IOFF

Output Leakage

IF5

Fail-Safe Output Leakage

Conditions

= 2V
= 7V
VIN = 0.4V
VIN = -7V
IOL = 50 rnA
VOUT = VEEVOUT = VEEVIN
VIN

(Inputs Open)
ILC

Output Clamp Leakage Current

Vc

Output Clamp Voltage

= GND
ICLAMP = -50 rnA

VOUT

Referenced to VEE-

Min

Typ

2.0

1.3

Max

Units
V

1.3

0.8

V

40
375

100
1000

p.A
p.A

-0.Q1
-1

-5
-100

p.A
p.A

-1.6

-2.1

V

-2

-100

p.A

-2

-100

p.A

2

100

p.A

-2

-1.2

V

1.2

V

Vp

Positive Output Clamp Voltage

ICLAMP = 50 mA
Referenced to GND

0.9

IEE(ON)

ON Supply Current

All Drivers ON

-2

-4.4

mA

IEE(OFF)

OFF Supply Current

All Drivers OFF

-1

-100

p.A

tpD(ON)

Propagation Delay to Driver ON

L = 1h, RL = 1k,
VIN = 3V Pulse

1

10

p's

L = 1h, RL = 1k,
10
p.s
1
VIN = 3V Pulse
Note 1: "Absolute Maximum Ratings" are those values beyond which the safety of the device cannot be guaranteed. Except for "Operating Temperature Range",
they are not meant to imply that the device should be oparated at these limits. The table of "Electrical Characteristics" provides conditions for actual device
tpD(OFF)

Propagation Delay to Driver OFF

operation.

Note 2: Unless otherwise specified, the minimax limits of the table of "Electrical Characteristics" apply within the range of the table of "Operating Conditions". All
typical values are given for VEE- ~ S2V, and TA ~ 2S'C.
Note 3: All current into device pins shown as positive, out of the device as negative. All voltages are referenced to ground unless otherwise noted.

5-36

Schematic Diagrams
15k

GND

----l
I
I

I
I

I
____ ...I

.........................._I!-oQVOUT

(1/4 CIRCUIT SHOWN)
TUF/S821-3

TUF/S821-4

III

5·37

~
In
~

r----------------------------------------------------------------------------,
~National

~
;; ~ Semiconductor
~ OS55451/2/3/4, OS75450/1/2/3/4 Series
~ Dual Peripheral Drivers
~

General Description

~

The 0875450 series of dual peripheral drivers is a family of
versatile devices designed for use in systems that use TTL
logic. Typical applications include high speed logic buffers,
power drivers, relay drivers, lamp drivers, M08 drivers, bus
drivers and memory drivers•
The 0875450 is a general purpose device featuring two
standard 8eries 54174 TTL gates and two uncommitted,
high current, high voltage NPN transistors. The device offers the system designer the flexibility of tailoring the circuit
to the application.

In

.....,...

I~

with the output of the logic gates internally connected to the
bases of the NPN output transistors.

Features
•
•
•
•
•
•
•
•

300 mA output current capability
High voltage outputs
No output latch-up at 20V
High speed switching
Choice of logic function
TTL compatible diode-clamped Inputs
8tandard supply voltages
Replaces TI "A" and "S" series

§

The 0855451/0875451, 0855452/0875452, 08554531
0875453 and 0855454/0875454 are dual peripheral ANO,
NANO, OR and NOR drivers, respectively, (positive logic)

~

Connection Diagrams (Oual-In-Llne and Metal Can Packages)

::t
In

i
~
i~

V2

A2

Vee

C2

82

11

E2

SUB

El

DND

10

~

In

....~.,...
In
~

In

~

VI

AI

Bl

Cl

TL/F/5824-1

Top View

Order Number DS75450N
See NS Package Number N14A

AI

82

A2

81

VI

V2

Vee

B2

V2

A2

Vee

82

A2

AI

81

VI

DND

TL/F/S824-2

Top View

TUF/5824-3

Vee

8Z

AZ

GND

AI

81

VI

TL/F/S824-4

Top View

Order Number DS55451J·8, Order Number DS55452J-8,
DS75451M or DS75451N
DS75452M or DS75452N
See NS Package Numbers J08A, M08A' or N08E

V2

V2

GND

TUF/S824-S

Top View

Top View

Order Number DS55453J-8,
DS75453M or DS75453N

Order Number DS55454J·8,
DS75454M or DS75454N

'See Note 6 and Appendix E regarding S.O. package power dissipation constraints.

5-38

Absolute Maximum Ratings

(Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage, (Veel (Note 2)
7.0V
Input Voltage
5.5V
Inter-Emitter Voltage (Note 3)
5.5V
Vee-to-Substrate Voltage
OS75450
35V
Collector-to-Substrate Voltage
OS75450
35V
Collector-Base Voltage
OS75450
35V
Collector-Emitter Voltage (Note 4)
OS75450
30V
Emitter-Base Voltage
OS75450
5.0V
Output Voltage (Note 5)
OS55451 IOS75451 , OS55452/0575452,
30V
OS55453/0S75453, OS55454/0S75454
Collector Current (Note 6)
OS75450
300mA
Output Current (Note 6)
OS55451 IOS75451 , OS55452/0S75452,
300mA
0555453/0S75453, OS55454/0S75454

OS75450 Maximum Power (Note 6)
Oissipation' at 25·C
Cavity Package
130BmW
1207mW
Molded Package
OS75451/2/3/4 Maximum Power (Note 6)
Oissipation t at 25·C
1090 mW
Cavity Package
Molded OIP Package
957mW
TO-5 Package
760mW
SO Package
632mW
-65·C to + 150·C
Storage Temperature Range
260·C
Lead Temperature (Soldering, 4 sec.)

Operating Conditions (Note 7)
Supply Voltage, (Veel
OS5545X
OS7545X
Temperature, (TAl
OS5545X
OS7545X

Min

Max

Units

4.5
4.75

5.5
5.25

V
V

-55
0

+125
+70

·C
·C

'Derate cavity package 8.7 mW/'C above 25'C; derate molded package
9.7 mWI'C above 25'C.
tOerate cavity package 7.3 mW/'C above 25'C; derate molded package
7.7 mW/'C above 25'C; derate T0-5 package 5.1 mWI'C above 25'C;
derate so package 7.56 mWI'e above 25'C.

Connection Diagrams (Oual-In-Line and Metal Can Packages) (Continued)
Vee

Vee

GND
Tl/F/5824-7

Tl/F/5824-8

Top View

Top View

Tl/F/5824-8

Top View
(Pin 4 is in Electrical Contact with the Case)

Order Number DS55451H

Order Number DS55452H
Order Number DS55453H
See NS Package Number H08C

Electrical Characteristics OS75450 (Notes Band 9)
Symbol

I

Parameter

I

IMin ITyp IMax IUnits

Conditions

TTL GATES
VIH

High Level Input Voltage

(Figure 1)

VIL

Low Levellnput Voltage

(Figure 2)

VI

Input Clamp Voltage

Vee = Min, II = -12 mA, (Figure 3)

VOH

High Level Output Voltage Vee = Min, VIL = O.BV,IOH = -400 /LA, (Figure2)

VOL

2

5-39

V

-1.5

V

2.4 3.3

V

0.22 0.4

Low Level Output Voltage Vee = Min, VIH = 2V, IOL = 16 mA (Figure 1)
Input Current at Maximum Vee = Max, VI = 5.5V, (Figure 4)
Input Voltage

V
O.B

Input A
InputG

V
mA

2

mA

•

Electrical Characteristics 0575450 (Notes 8 and 9) (Continued)
Symbol

I

Parameter

TTL GATES (Continued)

I

High Level Input Current Vcc

IIH

IMin ITyp IMax IUnits

Conditions

=

Max, VI

=

2.4V, (Figure 4)

III

Low Level Input Current Vcc

=

Max, VI

los

5hort Circuit
Output Current

Vcc

=

Max, (Figure 5), (Note 10)

ICCH

5upply Current

Vcc

5upply Current

Vee

=
=

Max, VI

ICCl

Max, VI

=

O.4V, (Figure 3)

=
=

Input A

40

/LA

InputG

80

/LA

Input A

-1.6 rnA

InputG

-3.2 rnA
-18

-55

mA

OV, Outputs High, (Figure 6)

2

4

mA

5V, Outputs Low, (Figure 6)

6

11

mA

OUTPUT TRANSISTORS
V(SR)CSO COllector-Base
Breakdown Voltage

Ic

=

100 /LA, IE

V(SR)CER COllector-Emitter
Breakdown Voltage

Ic

=

100/LA, RSE

V(SR)ESO Emitter-Base
Breakdown Voltage

IE

= 100/LA, Ic =

hFE

5tatic Forward Current
Transfer Ratio

VCE

=

=

0/LA

=

5000

O/LA

3V, (Note 11)

TA

TA

=

VSE

(Note 11)

5

V

25

Ic = 100mA

20

Is = 10mA, Ic

(Note 11)

V

30

Is
VCE(SAT) Collector-Emitter
5aturation Voltage

30

100mA

25

Ic = 300mA
Base-Emitter Voltage

V

Ic = 300mA

+25'C Ic

= O'C

=

35

=

=

100mA

0.85

1

30 mA, Ic = 300 mA

1.05 1.2

Is = 10mA, Ic = 100mA

0.25 0.4

18 = 30 mA, Ic = 300 mA

0.5

0.7

V
V
V
V

Electrical Characteristics (Continued)
0555451/0575451,0555452/0575452, 0555453/0575453,0555454/0575454 (Notes 8 and 9)
Symbol

Parameter

Conditions

Vil

Low-Level Input Voltage

VI

Input Clamp Voltage

Vcc = Min, II = -12 mA

VOL

Low-Level Output Voltage

Vcc = Min,
(Rgure7)

Vil = 0.8V

10l

=

100mA

10l = 300mA

VIH = 2V

10l = 100mA

10l = 300mA
High-Level Output Current Vcc = Min,
(Figure 7)

VOH = 30V VIH = 2V

Vil = 0.8V

II

Input Current at Maximum
Input Voltage

Max

2

High-Level Input Voltage

10H

Min Typ

(Figure 7)

VIH

Vcc = Max, VI = 5.5V, (Figure 9)

5-40

Units
V

0.8

V

-1.5

V

0555451,0555453

0.25

0.5

V

0575451, 0575453

0.25

0.4

V

0555451,0555453

0.5

0.8

V

0575451, 0575453

0.5

0.7

V

0555452, 0555454

0.25

0.5

V

0575452, 0575454

0.25

0.4

V

0555452, 0555454

0.5

0.8

V

0575452, 0575454

0.5

0.7

V

300

/LA

0575451, 0575453

100

/LA

0555452, 0555454

300

/LA

0575452, 0575454

100

/LA

1

mA

0555451, 0555453

m

Electrical Characteristics (Continued)

CJI

0555451/0575451, 0555452/0575452, 0555453/0575453, 0555454/0575454 (Notes 8 and 9) (Continued)
Symbol

Parameter

CJI

Min Typ

Conditions

Max

Units

40

p.A

-1.6

mA

IIH

High-Level Input Current

Vee = Max, VI = 2.4V, (Figure 9)

IlL

Low-Level Input Current

Vee = Max, VI = 0.4V, (Figure 8)

ICCH

5upply Current, Outputs High Vee = Max, VI = 5V
(Figure 10)
VI = OV

0555451/0575451

7

11

mA

0555452/0575452

11

14

mA

VI = 5V

0555453/0575453

8

11

mA

VI = OV

0555454/0575454

13

17

mA

Vee = Max, VI = OV
(Figure 10)
VI = 5V

0555451/0575451

52

65

mA

0555452/0575452

56

71

mA

VI = OV

0555453/0575453

54

68

mA

VI = 5V

0555454/0575454

61

79

mA

leeL

5upply Current, Outputs Low

Switching Characteristics 0575450 (Vee =

""'....
......

-1

5V, TA = 25°C)

c
en
CJI

CJI

""'
......
CJI
N

~

CJI
CJI

""'
CJI

.....
Co)

cen
CJI
CJI

""'
CJI

~

c
en
.....
CJI

""'......o
CJI

Symbol
tpLH

tpHL

Parameter
Propagation Oelay Time,
Low-to-High Level Output

Propagation Oelay Time,
High-to-Low Level Output

Conditions
CL=15pF

CL = 15pF

Min

Typ

Max Units

RL = 400n, TTL Gates, (Figure 12)

12

22

ns

RL = 50n, Ie ;:= 200 mA, Gates and
Transistors Combined, (Figure 14)

20

30

ns

RL = 400n, TTL Gates, (Figure 12)

8

15

ns

RL = 50n, Ie ;:= 200 mA, Gates and
Transistors Combined, (Figure 14)

20

30

ns

CL = 15 pF, RL = 50n, Ie ;:= 200 mA, Gates and
Transistors Combined, (Figure 14)

7

12

ns

tTHL

Transition Time, High-to-Low CL = 15 pF, RL = 50n, Ie ;:= 200 mA, Gates and
Level Output
Transistors Combined, (Figure 14)

9

15

ns

VOH

High-Level Output Voltage
after 5witching

Vs = 20V, Ie ;:= 300 mA, RSE = 500n, (Figure 15)

tD

Delay Time

tR

Rise Time

ts

5torage Time

Ie = 200 mA, IS(l) = 20 mA,
Is = -40 mA, VSE(OFF) = -1V,
CL = 15 pF, RL = 50n,
(FIgure 13), (Note 12)

tF

Full Time

mV
8

15

ns

12

20

ns

7

15

ns

6

15

ns

0555451/0575451, 0555452/0575452, OS55453/0575453, 0555454/0575454 (Vee = 5V, TA = 25°C)

tpHL

Parameter

Propagation Oelay Time, High-to-Low
Level Output

Conditions
CL = 15 pF, RL = 50n,
10 ;:= 200 mA, (Figure 14)

CL = 15 pF, RL = 50n,
10 ;:= 200 mA, (Figure 14)

Typ

Max

Units

0555451/0575451

Min

18

25

ns

0555452/0575452

26

35

ns

0555453/0575453

18

25

ns

0555454/0575454

27

35

ns

0555451/0575451

18

25

ns

0555452/0575452

24

35

ns

0555453/0575453

16

25

ns

0555454/0575454

24

35

ns

tTLH

Transition Time, Low-to-High Level
Output

CL = 15 pF, RL = 50n, 10 ;:= 200mA,
(Figure 14)

5

8

ns

tTHL

Transition Time, High-to-Low Level
Output

CL = 15 pF, RL = 50n, 10 ;:= 200 mA,
(Agure14)

7

12

ns

VOH

High-Level Output Voltage after
SWitching

Vs = 20V, 10;:= 300 mA, (Figure 15)

5-41

""'

CJI

N
......
~
.....
CJI

Vs - 6.5

Switching Characteristics (Continued)

Propagation Oelay Time, Low-to-High
Level Output

~
.....

CJI

Transition Time, Low-to-High
Level Output

tpLH

""'
....
......
CJI

tTLH

Symbol

c
en
.....
CJI

Vs - 6.5

mV

""'......
CJI

Co)

c
en
.....
CJI

""'
""'
CJI

~
Lt)

r------------------------------------------------------------------------------------------,

~

Switching Characteristics (Continued)

Jii
Q

Note 1: "Absolute Maximum Ratings" are those values beyond which the safety of the device cannot be guaranteed. Except for "Operating Temperature Range"
they are not meant to imply that the devices should be operated at these limits. The table of "Electrical Characteristics" provides conditions for actual device
operation.

Lt)
~

Note 2: Voltage values are wHh respect to network ground terminal unless otherwise specHied.

Lt)

......
C")

Ie

~
......
N
Lt)
~

Ie

~
......
.,...
Lt)
~

Ie

~
.....
CI
Lt)
~

Note 3: The vollage between two emillers of a mulliple... miller transistor.
Nole 4: Value applies when Ihe base-em iller resistance (RBe) Is squallo or less than

Note 6: Both halves of these dual circuHs may conduct rated current simultaneously; however, power dissipation averaged over a short time interval must fall within
the continuous dissipation rating.
Note 7: For the 0575450 only, the substrate (pin 8) must always be at the most-negative device voll8ge for proper operation.
Nole 8: Unless otherwise specified minImax limits apply across the - 55"C to + 125"C tempereture range for the 0555450 series and across the O"C to + 70"C
range for the 0575450 series. All typicals are given for Vee = + 5V and TA = 25"C.
Note 9: All currents into device pins shown as positive, out of device pins as negative, all vaHagas referenced to ground unless otherwise noted. All values shown
as max or min on absolute value basis.
Nole 10: Only one output at a time should be shorted.
Note 11: These parameters must be measured using pulse lechniques. tw

~

Lt)
~
Lt)
Lt)

~
.....
C")
~
Lt)
Lt)

~

~
~

Lt)
Lt)

~
.....
....

= 300 I's, duty cycle < 2%.

Note 12: Applies to output transistors only.

Truth Tables (H =

Ie

~
.....

soon.

Nole 5: The maximum voltage which should be applied to any outpul when H is in the "OFF" stale.

high level, L = low level)

0855451/0875451

0855453/0875453

A

B

Y

A

B

Y

L
L
H
H

L
H
L
H

L (ON State)
L (ON State)
L (ON State)
H (OFF State)

L
L
H
H

L
H
L
H

L(ONState)
H (OFF State)
H (OFF State)
H (OFF State)

0855452/0875452

0855454/0875454

A

B

Y

A

B

Y

L
L
H
H

L
H
L
H

H (OFF State)
H (OFF State)
H (OFF State)
L(ONState)

L
L
H
H

L
H
L
H

H (OFF State)
L(ONState)
L(ONState)
L (ON State)

Schematic Diagrams
0875450

~
Lt)

085545110875451

Lt)

~
.,o-.......--~r
L......._ _ _......_ ..........- -......-o •••

,--.....-p-+-......-I4-+-o·u'

Resistor values shown are nominal.

TLIF15824-11

0855452/0875452

"
"
.,0-++.....

Resistor values shown are nominal.

TL/F/5824-10
L-.....-

_ _....__......

...._ ......_o •• D

_~-4~

Resistor values shown are nominal.

5-42

TLIF15824-12

Schematic Diagrams (Continued)
0555453/0575453

0555454/0575454

~----.-----~---.-------ov~

~----.-----~---e--'--4~-----oV~

-----4----------......

_tI-O.N.

L......

Resistor values shown are nominal.

' -....- - - -......~--------..._tl_.........- -..._o 'N.
Resistor values shown are nominal.
TLlF/5824-14

TL/F/5824-13

DC Test Circuits

.iff~ .-

v,"

~

TL/F/5824-15

FIGURE 1. VIH. VOL

v,n;;;=;;.r-_

Each Input Is tested separately.

Each input is te.ted separately.

FIGURE 2. VIL. VOH

FIGURE 3. V" IlL

OPEN

v,

OPEN

TL/F/5824-19

TL/F/5824-18

v,"

TL/F/5624-17

TL/F/5824-16

Both Inputs are tested simultaneously.

Each input Is tested separately.

Each Input Is tested separately.

FIGURE 4.1" IIH

FIGURE 5. lOS

SEE

TEST

'ra.

FIGURE 6.ICCH. ICCL

Circuit

Input
Under
Test

0855451

VOH

~IDL

TABLE

TL/F/5824-20

Both gates are tested simultaneously.

0855452

Output

Other
Input

Apply

VIH

VIH

VOH

IOH

VIL

Vee

IOL

VOL

Measure

VIH

VIH

IOL

VOL

VIL

Vee

VOH

IOH

VIH

Gnd

VOH

IOH

VIL

VIL

IOL

VOH

VIH

Gnd

IOL

VOL

VIL

VIL

VOH

IOH

VaL

li

0855453

':' ':"

TL/F/5624-21

0855454

FIGURE 7. VIH. Vlu 10H. VOL

5-43

•

DC Test Circuits (Continued)
v'"
4.&V

SEE
NOTES

A.B

.-.....L_.,
CIRCUIT
UNDER
TEST

v'"
V
OPEN
OPEN

Note A: Each input is tested separately.
Note B: When testing 0555453/0575453,
0555454/0575454, Input nol
under leslls grounded.
For all other circuits H is at 4.5V.

Each input is lested seperelely.

TLlF/5824-22

OPEN

Vee

TUF/5824-23

FIGURE 9. 110 IIH

FIGURE 8. Vb Vil

OPEN

Vee

v,"-..L...........

v,

-=

Both gales are lested simultaneously.

Bolh gales are tesled simultaneously.

TUF/5824-24

FIGURE 10.ICCH, ICCl for AND, NAND Circuits

-=

AC Test Circuits and Switching Time Waveforms
INPUT

2.4V

Vee

OUTPUT

5V

RL -400
·All diades.ue 1N3G64
GNo

CL 1:16pF

~INoTE21

TUF/5824-26

tI~&M

M.""....---~IDM

IA'~ .

ao:.5~1

INPUT

3V

~-D.-....____l;';D_%__"'_;"'_--!i-_-_-+-_-",,-,--- DV

OUTPUT

~'" ~

'\L~.5V

VOH

","-Va'

_ _ _ _ _J.

TUF/5824-27

Note 1: The pulse generalor has Ihe following characteristics: PRR

TUF/5824-25

FIGURE 11.ICCH, ICCl for OR, NOR Circuits

= 1 MHz, ZOUT

'" 50n.

Note 2: CL Includes probe and jig capacitance.

FIGURE 12. Propagation Delay Times, Each Gate (D575450 Only)

5·44

AC Test Circuits and Switching Time Waveforms

~
en

(Continued)

en
-'="
en
-a.

10V
INPUT

.....
c
en

-IV

...- -....-

...-

en
en
-'="
en

OUTPUT

N
......

CL =15pF

~
en

l(NOTE2)

TL/F/S824-28

1-- "'-----1

INPUT~81~'~ ~~~.:_::
::;5nl

..

"1
1~~

OUTPUT

en
en
-'="
en
-'="
......

S5n!

c

en
......

.,-J

en
-'="
en

1{J.,"'10"'%-----

TLlF/S824-29

Note 1: The pulse generator has the fonowing characteristics: duty cycle,,; 1 %, ZOUT '" son.

FIGURE 13. Switching Times, Each Transistor (0575450 Only)
2.4V

«:)
......
cen
......

en
-'="
en
-a.

Note 2: CL includes probe and iig capacitance.
INPUT

w
......

~

0•3

'.

en
-'="
en

......

.OY

l

~
......
en
-'=>
en

....-

N
......
C
en
......

.....-oOUTPUT

en
-'="
en

OS55453

54
I 055r

'":"

w
......

* ":"

C

~-'="

DAY

NOle 1: The pulse generator has the fonowing characteristics: PRR

~

en
-'="

TLlF/S824-30

1.0 MHz, ZOUT '" son.

Note 2: CL includes probe and jig capacitance.
Note 3: When testing D575450, connect output V to transistor base and ground the substrate terminal.

lr.::::;------3.0V
INPUT
DSl54SO
OS554&1
D5&5453

i--------O.6ps-------i
::;5.00$

J,.."",...-------------:=Ii-H--------3.0V

'\.::"'-----OV

VOH
OUTPUT

~~--------------~~+_----'VOL
TUF/S824-31

FIGURE 14. Switching Times of Complete Drivers

5-45

~

~

§

r---------------------------------------------------------------------------------,
AC Test Circuits and Switching Time Waveforms (Continued)

c;;
II)
~

2.4V

INPUT

~

.1,

~
.....
N

II)
~

J~
65

"""""-"'-0

~

(NOTE I)

§

OS55453

UNOER
TEST
(NOTE 2)
OND

• OSlif54 • ':'

~

DAV

~

§

=1 rs&n.

~

II)

~

1

f--S&"

INPUT J,iBO%

~

~:=

~
~

IT

OUTPUT

~~CL·'5pF

I SUB

(NOTE 3)

I

~

";:-

l

TL/F/5824-32

r-

SID

..

3V

DJ~~~~ ~ ~
I_~:~
~::~ '~Vl\L~,O%~4~;;::::::::UB~;tr:---~..----------~

:;;:

....
,..

__r:jr,1

OE:~~~OR 1l-!-_--l~fic~IR~CU~ITy-

II)
~

~

~ 2mH

IN3DB4

OS55451
OS55452

§.....,..

II)

~{

.

-I

Il--slDn.

----....,B:;;Oii!"l~i:++--.::........;.,.----3V

1.&V

1.&V

10%

11l% _ _ _ _ _ OV

\

OUTPUT

Note 1: The pulse generator has the following characteristics: PRR = 12.5 kHz, ZOUT '" 500.
TL/F/5824-33
Note 2: When testing 0575450, connect output V to transistor base with a 6000 resistor from there to ground and ground the substrate terminal.
Note 3: CL Includes probe and Jig capacitance•

FIGURE 15, Latch-UP Test of Complete DrIvers

~

II)
II)

~

Typical Performance Characteristics
4.0

1

r-r-"'T"""'T"""'''''''-Y-'''''''

Q

tOO

!ia:

a:

iI!

!ii
...

."
i
.!i
a:
a:

I I

VeE·3V

--

(NOTE 8)
80
80
40

......

I,..-

TA-+7D'~_

TA-~-

10-

,J......I
TA-D'C:-

Q

-to

-20

-30

a:

20

it

0

Ii>

HIGH·LEVEL OUTPUT CURRENT (mAl

10

20
40 70 100 200
COLLECTOR CURRENT (mA)

400
TL/F/5824-35

TL/F/5824-34

FIGURE 17. OS75450 TransIstor StatIc Forward Current
Transfer RatIo vs Collector Current

FIGURE 16. OS75450 TTL Gate HIgh-Level Output
Voltage vs Hlgh-Lavel Output Current

5-46

Typical Performance Characteristics

(Continued)
~

~

Ie
i;"10

1.0

~

O.B

~
a:

0.6

~

OA

!

0.2

~

~

TA=+70"C

.~
I
~

::::::::::: ~ TA"'" +25-C

S

o
10

0.6
0.5

!:;
co
z
co

TA=~

INOTE 8)

w

~

>

20
40 70 100 200
COLLECTOR CURRENT (mA)

400

!£

I.

= 10

INOTE 8)
0.4
0.3
0.2
0.1
0
10

20
40 70 100
200
COLLECTOR CURRENT ImA)

400

TL/F/5824-36

TLlF/5824-37

FIGURE 18. 0575450 Transistor Base-Emitter
Voltage vs Collector Current

FIGURE 19. Transistor Collector-Emitter Saturation
Voltage vs Collector Current

Typical Applications
AZO------,
+5V

14

13

12

11

10

SUB

+V

y

OS75450

GNO
G

Alo----..J
Y :: G+ A1 • AZ + Ai

. A2
TLlF/5824-38

FIGURE 20. Gated Comparator

+5V

10

11

SUB

+V

....1-.....- 0

OS75450

OUTPUT

GNO
INPUT G
INPUT A0--+---..1
TL/F/5824-39

FIGURE 21. 500 rnA Sink

5-47

~
II)
~
II)

.-------------------------------------------------------------------------------------------,
Typical Applications

iii
c

+VI

(Continued)

o-------.....

-_~M,....--------oOUT·OF·PHASE

~
II)

OUTPUT

. - - -.....- - 0 IN.pHASE OUTPUT

~

INPUT

&3

0----.....,
-V2

+5V

c

10

B

~

SUB

~
~

~
.....
..II)
~

~

(/)

c
.....

STROBE

This side can perform the same or another function.

CI

II)
~

~

en

,v

c

;;:

It

.,.

Uk

II)
~
II)
II)

O)~

Uk

1/0.',.. "
1\
OUTPUT 0

~
.....
CW)

14

~

II)
II)

~
.....

'"

II)
~
II)
II)

'--

~
.....
..-

13

~
•

2

IZ

.0

11

I

•

SUI

~

DS7545G

---c-

3

•

• •

GN.

I'
OUTPUT

II)
~
II)

~

TL/F/5824-40

FIGURE 22. Floating Switch

n
TLlF/5824-41

FIGURE 23. Square-Wave Generator
+VlO-....._ _ _ _ _....._ ....._.....,

+'V

....

---------,I
DIODE ARRAY

I
I
I
I

J
I SOURCE

t CURRENT
STROBE

TO MEMORY DRIVE LINES

'--+----o-V2
Source and sink controls are activated by
high-level input voRages (VIH :.: 2V).
TL/F/5824-42

FIGURE 24. Core Memory Driver

5·48

Typical Applications (Continued)
+5vo----.-------------------------------t----,
4.7k
r----t----~--~r_~OUTPUTA

INPUT A o----t----,
II

10

-IOV OR NEGATIVE
SUPPl Y OR MOS CIRCUIT

0575450

GNO
STROBE
L----t----+-----j~_o

OUTPUT B

INPUT Bo----------'
4.7k

IN759

TlIF/5824-43

FIGURE 25. Dual TIL-to-MOS Driver
+5Vo---------.-~~--------------t_--_1~------------__,

22k

2.7k

r----4----~--------------_;--~OUTPUTA

INPUT A

0--9-'V33VkIf--'

DS75452

390

I

"D"

TEST

390

TL/F/5B24-4B

FIGURE 30. TTL or DTL Positive Logic-Level Detector
5Vo-~--~r------1~-----------------------'--~--~~

10k"

DS75452

390
30k"
470

INPUT

'The IWo Input resistor. must be adjusted for the level of MOS Input.

TL/F/5B24-49

FIGURE 31. MOS Negative Logic-Level Detector
5Vo-------~----------------------_,
lk

INPUT A

STROBE

•

0575453

INPUT B

TL/F/5B24-5D

FIGURE 32. Logic Signal Comparator

5-51

~ r-------------------------------------------------------------------------------~

.."
~

&i
c

Typical Applications (Continued)

c:;

5Vo-------~----------------------~

.."
~

~

A

Ik

-+___--,

SIGNALS FROM}
PEAK OETECTORS 0-'11'--_ _

t---.() OUTPUT

......
('I
.."
~

.."

~.,..
......

0575453

.."
~

Ie

~

C>
.."

4

I"

~

'If Inputs are unused. they should be connected 10

.."

+ 5V through a 1k r;;sistor.

TL/F/5824-51

In
c
~
.."
~

H

:g

A

~

c:;

H

.."
~

.."

.."

~

T~/F/5824-52

Low output occurs only when inputs are low simultaneously.

~

.."
.."

~
......
.,..

~-------------H

OUTPUT

~

FIGURE 33. In·Phase Detector

5V

.."
~

Ik

.."
.."

Ik

VI

~

8

7

6

=Aii

VI=A.B

5

INPUT A 0-INPUT B0 - -

0576464

~

p--c

INPUTC 0--

-

1

2

3

V2 =VI. C= (A. BI C
Y2 =VI+ C = Aii. C

4

TLlF/5824-53

FIGURE 34. Multifunction Loglc-5ignal Comparator

5-52

Typical Applications

(Continued)

5Vo-----------~------------------------._--~
FROM ALARM {
TRANSDUCERS

ALARM
RElAY

0-+--.....-----1--------,
390

390

,-"'-------+--------+'-------1"'-1

DS75454

FROM ALARM {
TRANSDUCERS

0-+--..,.------------....1
390

19D
TUF/5824-54

FIGURE 35. Alarm Detector

•
5·53

Section 6
High Current Switches

Section 6 Contents
High Current Switch Selection Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM1921 1 Amp Industrial Switch. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LM1950 750 mA High Side Switch....................................................
LM 1951 Solid State 1 Amp Switch . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
LMD18400 Quad High Side Driver . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

6-2

6-3
6-4
6-9
6-14
6-22

x

cC'
::s-

~National

O

...n;c

Semiconductor

::I

~
g:

High Current Switch Selection Guide

::s(J)
(1)

CD
Device
LM1921

Driversl
Package

Continuous
Current

Peak
Current

Input Voltage
Range'

1

1.0A

2.0A

4.5Vto26V

Diagnostics
None

Page
No.
6-4

LM1950

1

750mA

l.4A

4.75Vto26V

None

6-9

LM1951

1

1.0A

2.5A

4.5Vto 26V

Error Flag

6-14

LMD18400

4

1.0A

3.0A

6Vto 26V

Error Flag
Thermal Shutdown Flag
Data Output provides switch
status feedback, output
load fault conditions
and thermal and
overvoltage shutdown status.

6·22

• All devices incorporate Automotive transient protection.

6-3

~

O·

::I
C)
C

a:
(1)

~

~
~

:::E

....I

r------------------------------------------------------------------------------------,

~National

~ semiconductor

LM19211 Amp Industrial Switch
General Description

Features

The LM1921 Relay Driver incorporates an integrated power
PNP transistor as the main driving element. The advantages
of this over previous integrated circuits employing NPN
power elements are several. Greater output voltages are
available off the same supply for driving grounded loads;
typically 4.5 volts for a 500 mA load from a 5.0 volt supply.
The output can swing below ground potential up to 57 volts
negative with respect to the positive power supply. This can
be used to facilitate rapid decay times in inductive loads.
Also, the IC is immune to negative supply voltages or transients. The inherent Safe Operating Area of the lateral PNP
allows use of the IC as a bulb driver or for capacitive loads.
Familiar integrated circuit features such as short circuit protection and thermal shutdown are also provided. The input
voltage threshold levels are designed to be TTL, CMOS,
and LSTTL compatible over the entire operating temperature range. If several drivers are used in a system, their
inputs andlor outputs may be combined and wired together
if their supply voltages are also common.

• 1 Amp output drive
• Load connected to ground
• Low input-output voltage differential
• + 60 volt positive transient protection
• - 50 volt negative transient protection
• Automotive reverse battery protection
• Short circuit proof
• Internal thermal overload protection
• Unclamped output for fast decay times
• TTL, LSTTL, CMOS compatible input
• Plastic TO-220 package
• 100% electrical burn-in

Applications
•
•
•
•
•
•

Relays
Solenoids
Valves
Motors
Lamps
Heaters

Typical Application Circuit
Vee

voN/OioFFFF' OO----::::-:---....::.t

'Required for stability
TUH/5271-1

FIGURE 1_ Test and Application Circuit

Connection Diagram
TO·220 5 LEAD

I~I

~ ""I'"
4 GROUND
3 GROUND

2 OUTPUT (Voull
1 SUPPLY (Veel

I

TL/H/5271-2

Front View
Order Number LM1921T
See NS Package Number T05A

6-4

Absolute Maximum Ratings
If MIlitary/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage
Operating Range
4.75Vt026V
Overvoltage Protection (100 ms)
-50Vto +SOV

Internal Power Dissipation

Internally Limited
-40·C to + 125·C

Operating Temperature Range
Maximum Junction Temperature

~
....
CD
N
....

150"C
-S5·C to + 150"C

Storage Temperature Range
Lead Temp. (Soldering, 10 seconds)

230"C

Electrical Characteristics (Vee = 12V, IOUT= 500 mA, TJ=25·C, VON/OFF=2V, unless otherwise specified.)
Parameter
Supply Voltage
Operational
Survival
Transient

Conditions

Typ

100 ms, 1% Duty Cycle

Tested Limits
(Note 1)

Design Umlts
(Note 2)

Min

Max

Min

Max

4.75
-15
-50

26
60

6

24

Units

V
VOe
V

Supply Current
VON/~=O
VON/~=2V

Input to Output
Voltage Drop

IOUT=OmA
IOUT=250 mA
IOUT=500mA
IOUT=1A

0.6
6
285
575
1.3

IOUT=500 mA
IOUT=1A

0.5
1.0

Short Circuit Current

1.4

1.5
10
350
700
1.5
0.8
1.0

Output Leakage Current
ON/OFF Voltage
Threshhold

0.8

ON/OFF Current

15

Overvoltage Shutdown

32

VON/OFF=O, IOUT=100 rnA

Fault Conditions
Output Current
ON/OFF Floating
Ground Floating
Reverse Voltage
Reverse Transient
Overvoltage
Supply Current

Pin 5 Open
Pin 3 & Pin 4 Open
Vee= -15V
Vee=-50V
Vee=+60V
Pin 1 & Pin 2 Short, No load

50

""A

0.8

2.0

V
V

26

36

2.0

6V~Vee~24V

Inductive Clamp
Output Voltage

A
A

0.1
1.3

/ljc
/lca

3.0

.75

VON/OFF=O

Thermal Resistance
junction-case
case-ambient

V
V

2.0

6V~Vee~24V

10

30

""A

0.1
0.1
-0.Q1
-100
0.Q1
10

V
·C/W
·C/W

3
50
-SO

mA
mA
rnA
mA
A

-120

-45

V

50
50

,.,.A

-1
1
40

""A
mA
mA
mA
mA

Note 1: Guaranteed and 100% production tested.
Note 2: Guaranteed, not necessarily 100% production tested. Not used to calculate outgoing AQL. Limits are for the temperature range of - 40'C,. TJ" 150'C.

6-5

•

Typical Performance Characteristics
Output Voltage Drop

...~
c::>
c::>

II:

Device Operating Current

0.8

~

~

!:l'"
...

-

0.6

lOUT = 500mA

::I
::I

c::>
I

=--

0.2

~

o

lOUT

LooJ
o 1-'"

o

40

200

400

600

~

c::>

800

35

i

o

,

o

1..1'

100

1..1'

~o

,"

~

25
20

~

IS
10

:l
B 15

I~

"z
o

10
5

20

I

I

12

30

~ .... ~HrT'INK,- f~

4
2

o

0
W 40
SUPPLY VOLTAGE(VI

-~

~

---

I I

10

I ...
o

NO HEAT SINK

I'

10 2D 30 40 50 60 70 80 90
AMBIENT TEMPERATURE ('CI
TL/H/5271-B

TUH/5271-7

Threshold Voltage vs.
Supply Voltage
_1.50

ON/OFF Current vs.
ON/OFF Voltage
30

e

Ii us

L

~ 1.40
~

iB 1.35

.. ...

j!: 1.30

I~ 1.25
1.20
25

50

75 100 125

JUNCTION TEMPERATURE ('CI

r

'-40'C

o

10

15

2D

I--

o
25 30

SUPPLY VOIl'AGE (VI

,.'

vecruv r--

o

1

2

3

4

5

ON/OFr VOIl'AGE (VI
TUH/5271-14

TL/H/5271 - I 3

VCC=26V

t r- r-

..: .'::'.:: -=,:' - -

~

o

--

125'\ 25'C

II:

0

I-

E5 14

1/

-40

IN~INAE

I--- I- HEAT SINK I-

~ 16

-10

300 400 SOD 600 700 800

-

-50 -25

25

Maximum Power
Dissipation (TO-220)

-5

ON/OFF Current vs.
Junction Temperature

20

20

TL/H/5271-5

~

TLlH/5271-6

15

15

Vee (VI

1/

OUTPUT CURRENT(mAI

1

10

18 1 - - r-

VON/OFFa2V

I:

30 VCCa12V
VIN=2V
26

oo

1000

JL~5J!l I

30

~

~

I

Output Voltage (VOUT)

1/
~

I

0.5

TUH/5271-4

Output Voltage Drop
1.0
0.9
CL.
0.8
~ 0.7
~ 0.6
0.5
~ 0.4
~ 0.3
<;' 0.2
>B 0.1

"

1.0

OUTPUT CURRENT (mAl

TUH/5271-3

e

~

1.5

I-

~

~I"

aD
120 160
JUNCTION TEMPERATURE('CI

-40

i

E!

~

0.4

I-

5
II:

c::>

:-

I-

Peak Output Current (VOUT)

400

Equivalent Block Diagram

9

TUH/5271-15

Vee

veeO----1~----------~--------------------------t_~

ON!OFr

5

3

4

2

OUT
100 nF

OUTPUT

TUH/5271-12

FIGURE 1
6-6

0

::;'

n

C

Vee

::;:

en
n
014

:::r

I¥""---

CD

..

3SI)

(;'
VoUT

~I

I

r·'

54o~
R17

I

~R6
60k

-=-

~R8

33k

19k~Rn

18k .... RID

3;R12
700

I

R16
400

R15

30k

6NOO

hU
20k

,

.,

03

25k! R4

25k

---

f

I I

~023 1:1

24k

ON/Off

024

R13

"nn

R18

IN
lk

R5

•

~'8UZ~022
22k
22k

f~14

I
TL/H/5271-9

~l:6~W'

9- ~-----------------------------------------------------------------------------------------,

~

9-

:5

Application Hints
combined zener and diode breakdown should be less than
45 volts.

HIGH CURRENT OUTPUT
The 1 Amp output is fault protected against overvoltage. If
the supply voltage rises above approximately 30 volts, the
output will automatically shut down. This protects the internal circuitry and enables the IC to survive higher voltage
transients than would otherwise be expected. The 1921 will
survive transients and DC voltages up to 60 volts on the
supply. The output remains off during this time, independent
of the state of the Input logic voltage. This protects the load.
The high current output is also protected against short circuits to either ground or supply voltage. Standard thermal
shutdown circuits are employed to protect the 1921 from
over heating.

The LM1921 can be used alone as a simple relay or solenoid driver where a rapid decay of the load current is desired, but the exact rate of decay is not critical to the system. If the output is unclamped as in Figure 1, and the load
is inductive enough, the negative flyback transient will cause
the output of the IC to breakdown and behave similarly to a
zener clamp. Relying upon the IC breakdown is practical,
and will not damage or degrade the IC in any way. There are
two considerations that must be accounted for when the
driver is operated in this mode. The IC breakdown voltage is
process and lot dependent. Clamp voltages ranging from
- 60 to -120 volts (with respect to the supply voltage) will
be encountered over time on different devices. This is not at
all critical in most applications. An important consideration,
however, is the additional heat dissipated in the Ie as a
result. This must be added to normal device dissipation
when considering junction temperatures and heat sinking
requirements. Worst case for the additional dissipation can
be approximated as:

FLYBACK RESPONSE
Since the 1921 is designed to drive Inductive as well as any
other type of load, inductive kickback can be expected
whenever the output changes state from on to off (see
waveforms on Figure 1). The driver output was left unclamped since it is often desirable in many systems to
achieve a very rapid decay in the load current. In applications where this is not true, such as in Figure 2, a simple
external diode clamp will suffice. In this application, the Integrated current in the inductive load is controlled by varying
the duty cycle of the Input to the driver IC. This technique
achieves response characteristics that are desirable for certain automotive transmission solenoids, for example.

Additional Po = 12 X Lx f (Watts)
where:

I = peak solenoid current (Amps)
L = solenoid inductance (Henries)
f = maximum frequency input Signal (Hz)

For solenoids where the Inductance Is less than ten millihenries, the additional power dissipation can be ignored.

For applications requiring a rapid controlled decay in the
solenoid current, such as fuel injector drivers, an external
zener and diode can be used as In Figure 3. The voltage
rating of the zener should be such that it breaks down before the output of the LM1921. The minimum output breakdown voltage of the IC output is rated at -57 volts with
respect to the supply voltage. Thus, on a 12 volt supply, the

Overshoot, undershoot, and ringing can occur on certain
loads. The simple solution Is to lower the Q of the load by
the addition of a resistor in parallel or series with the load. A
value that draws one tenth of the current or DC voltage of
the load is usually sufficient.

Dulput

DulpUI

~ ~'N4DD'

TL/H/5271-10

TLlH/5271-11

FIGURE 2. Diode Clamp

FIGURES
Zener clamp for rapid conlrolled currenl decay

6-8

r

:s::
......

~National

CD

U'1

~ Semiconductor

o

LM 1950 750 rnA High Side Switch
General Description

Features

The LM1950 is a high current, high side (PNP) power switch
for driving ground referenced loads. Intended for industrial
and automotive applications the LM1950 is guaranteed to
deliver 750 mA continuous load current (with typically 1.4
Amps peak) and can withstand supply voltage transients up
to +60V and -50V. When switched OFF the quiescent
current drain from the input power supply is less than
100 ",A which can allow continuous connection to a battery
power source.
The LM1950 will drive all types of resistive or reactive loads.
To obtain a rapid decay time of the energy in inductive
loads, the output is internally protected but not clamped and
can swing below ground to at least 54V negative with respect to the input power supply voltage.

•
•
•
•
•
•
•
•
•
•
•

The ON/OFF input can be driven with standard 5V TTL or
CMOS compatible logic levels independent of the Vee supply voltage used. Built in protection features include short
circuit protection, thermal shutdown, over-voltage shutdown
to protect load circuits and protection against reverse polarity input connections. The LM1950 is available in a 5-lead
power TO-220 package and specified over a wide - 40'C to
125'C operating temperature range.

• Relay driver
III SolenoidlValve driver

Typical Application

750 mA continuous output drive current
Less than 100 ",A quiescent current in OFF state
Low input! output voltage drop
+60V/-50V transient protection
Drives resistive or reactive loads
Unclamped output for fast inductive decay tmies
Reverse battery protected
Short circuit proof
Overvoltage shutdown to protect loads
TTL/CMOS compatible control input
Thermal overload protection

Applications
• Lamp driver
• Load circuit switching
• Motor driver

+4.75 TO 26V

O.l/JF

I

ve}-

Vee SUPPLY
1

ov
ON

r-l °ON~fffiT_OF_F~__________i
..J Lov 5

+ 5V

Vee - 54V

OFF

OUTPUT

I liS

-------+-+--------'.,.,.
GROUND

4

3

GROUND

RELAY
LOAD

TLlH/11237-1

'Required for stability

Connection Diagram
TO 220, 5 Lead

!' '",."

4 GROUND
3 GROUND

, '"W"' ('(Vee)
•.,J
1 SUPPLY

TLlH/11237-2

Front View
Order Number LM1950T
See NS Package Number T05A

6-9

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.

Storage Temperature Range
Lead Temperature
(Soldering, 10 seconds)

230·C

Supply Voltage
Continuous
Transient(T:S; 100ms)
Reverse Polarity (continuous)

ESD Susceptibility (Note 2)

2000V

26V
-SOVto +60V
-15V

On/Off Voltage

-0.3Vto +6.0V

Power Dissipation

Internally Limited

Load Inductance

Operating Ratings (Note 1)
-40·Cto +12S·C

Temperature Range (TAl

4.7SVt026V

Supply Voltage Range
Thermal Resistances:
Junction to Case (8j.C>
Case to Ambient (8e-a>

1S0mH

Maximum Junction Temperature

-6S·Cto +1SO"C

1S0·C

3·C/W
50·C/W

Electrical Characteristics
Vcc = 14V, lOUT = 150 mA unless otherwise indicated. Boldface limits apply over the entire operating temperature range,
-40"C :s; TA :s; 125·C, all other speCifications are for TA = TJ = 25·C
Parameter

Conditions

Limit

Units
(Limit)

4.75/4.75
26/26
-15/-15
60/60
-50/-50

V (Min)
V (Max)
Voc(Min)
V (Max)
V (Min)

20

100/100

"A(Max)

5
275
550
825

10/10
350/350
700/700
950/950

mA(Max)
mA(Max)
mA(Max)
mA(Max)

0.30
0.50
0.75

0.5/0.6
0.7/1.0
1.1/1.4

V (Max)
V (Max)
V (Max)

1.5

1.0/0.75
2.0/2.0

A (Min)
A (Max)

Typical

Supply Voltage
Operational
Survival
Transient
Supply Current

Input to Output
Voltage Drop

t = 1 ms, T = 100 ms,
1 % dutycycle
VON/OFF
VON/OA'
lOUT =
lOUT =
lOUT =
lOUT =

= 0.8V
= 2.0V

OmA
2S0mA
SOOmA
750mA

lOUT = 250mA
lOUT = 500mA
lOUT = 7S0 mA

Short Circuit Current
Output Leakage Current

VON/OFF = 0.8V

ON/OFF Input
Threshold Voltage
ON/OFF Input Current

VON/OA' = 0.8V
VON/OFF = 2.0V
VON/Off = 5.25V

Overvoltage Shutdown
Threshold

10

50/50

"A (Max)

1.4

0.8/0.B
2.0/2.0

V (Min)
V (Max)

0.1
1
50

5/10
10/20
100/100

"A (Max)
I£A (Max)

33

27/27
37/37

V (Min)
V (Max)

"A (Max)

Inductive Clamp
Output Voltage

VON/OFF = 2V to 0.8V,
lOUT = 100 mA

-45

-120/-120
-40/-40

V (Max)
V (Min)

Output Turn·On Delay

VON/Off 0.8V to 2V

4.2

20

p.s

Output Turn·Off Delay

VON/OFF 2V to 0.8V

4.5

20

"S

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions fot which the device is
intended to be functional, but do not guarantee specific performance limits. For guaranteed specHications and test conditions, see the Electrical Characteristics.
Note 2: Human body model, 100 pF discharged through a 1.5 kn resistor.

6·10

...is:
.....

Typical Performance Characteristics

CD

U\

Output Voltage Drop
vs Temperature

Output Voltage vs Vee
35

f1t. =

30
25

E

son

1.0

t

E

VON/orr = 2V

~

15

g

~
g

~

~

1/

.}

-5
-40

-20

0

20

40

-40

40

SUPPLY VOLTAGE (V)

./

i

,

/'

40

/'

o
10

15

20

25

"

o

30

VCC (V)

ON/OFF Input Current
vs ON/OFF Input Voltage

~

20

/

~

=

~

600

400

10

o
o

-

II~

10 20 30 40 50 60 70 80 90

On/OFF Input Threshold
Voltage vs Supply Voltage

E
~

/

/

1.40

~

1.35

~S

o
40

80

120

160

~

-

-4~!c - -25~C

1.30
1.25
1.20

-40

r-- r--

1.45

~
g

~

/
V"

INPUT VOLTAGE (V)

..... roo

NO HEAT SINK

AMBIENT TEMPERATURE (OC)

I

./

~ i""-< ~/~H~TSI"K I-- I--

OUTPUT CURRENT (mA)

/

'-

I I
I I

o
o

800

r-r-

HEAT SINK

12
10

2

200

IJrINI~E -

r-r- -

16
14

I

V

Vee = I2V
VON/orr = 2V

";("

30

S

10

40

100 200 300 400 500 600 700 800

1.50

50

~

:g

ON/OFF Input Current
vs Temperature

60

.5

0.1

o

~

/

20

o

/

V

/'

OUTPUT CURRENT (mA)

V

60

~

I

o

""

0.3
0.2

20
18

.§

I
f

0.5

0.5
0.4

Maximum Power
Dissipation

80

";("

V

1.0

V
/'

oV

160

100

1.5

~

120

0.8
0.7
0.6

Operating Current
vs Load Current

2

~~

80

1.0
0.9

JUNCTION TEMPERATURE (oc)

Peak Output Current

3

~
'i'
.}

I

o

60

~

I

0.2

-10

~

= 100 mA

lOUT

?

~
~
g

I

= 500 mA

I

0.4

~

Output Voltage Drop
vs Output Current

E

I

lOUT

0.6

~

I

10

~

0.8

~

II

20

I

o

o

10

15

20

25

30

SUPPLY VOLTAGE (V)

JUNCTION TEMPERATURE (OC)

TLlH/11237-3

Turn-On Delay Time
vs Temperature

Turn-Off Delay Time
vs Temperature

8.0
7.0

7.0

ON!OrF

6.0

6.0

INPUT

1

./

5.0

4.0

~

:2

;:::

Delay Time Definitions

8.0

I-3.0

5.0
4.0

~

:2

;:::

3.0

2.0

2.0

1.0

1.0

o
-40

--

1

V

-- -

80

120

160

JUNCTION TEYPERATURE (oe)

-40

ON

OV:

:

o

o
0

'oN - - ' ; . V
OUT

OV

0

40

80

120

160

JUNCTION TEMPERATURE (oc)
TL/H/11237-12

TLlH/11237-11

6-11

0

V

~o:
OCC go %
0

10%

0 0
0

torr

o
40

+5V

~

-!

0

~

TLlH/11237-10

Application Hints
The LM1950 can be used alone as a simple relay or solenoid driver where a rapid decay of the load current is desired, but the exact rate of decay is not critical to the system. If the output is unclamped as in Rgure 1, and the load
is inductive enough, the negative flyback transient will cause
the output of the IC to breakdown and behave similarly to a
zener clamp. Relying upon the IC breakdown is practical
and will not damage or degrade the IC in any way. There are
two considerations that must be accounted for when the
driver is operated in this mode. The IC breakdown voltage is
process and lot dependent. Output clamp voltages ranging
from -40V to -120V (with Vee supply of 14V) will be encountered over time on different devices. This is not at all
critical in most applications. An important consideration,
however, is the additional heat disSipated in the IC as a
result. This must be added to normal device dissipation
when considering junction temperatures and heat sinking
requirements. Worst case for the additional dissipation can
be approximated as:
Additional PD = 12 X Lx f(Watts)

HIGH CURRENT OUTPUT
The 750 mA output is fault protected against overvoltage. If
the supply voltage rises above approximately 30V, the output will automatically shut down. This protects the internal
circuitry and enables the IC to survive higher voltage transients than would otherwise be expected. The LM1950 will
survive transients and DC voltages up to 60V on the supply.
The output remains off during this time, independent of the
state of the input logic voltage. This protects the load. The
high current output is also protected against short circuits to
either ground or supply voltage. Standard thermal shutdown
circuits are employed to protect the LM1950 from over heating.
FLYBACK RESPONSE
Since the LM1950 is designed to drive inductive as well as
any other type of load, inductive kickback can be expected
whenever the output changes state from ON to OFF (See
Waveform on Figure 1). The driver output was left unclamped since it is often desirable in many systems to
achieve a very rapid decay in the load current. In applications where this is not true, such as in Figure 2, a simple
external diode clamp will suffice. In this application, the integrated current in the inductive load is controlled by varying
the duty cycle of the input to the drive IC. This technique
achieves response characteristics that are desirable for certain automotive' transmission solenoids, for example.

Where: I = Peak Solenoid Current (Amps)
L = Solenoid Inductance (Henries)
f = Maximum Frequency Input Signal (Hz)
For solenoids where the inductance is less than ten millihenries, the additional power dissipation can be ignored.
Overshoot, undershoot, and ringing can occur on certain
loads. The simple solution is to lower the Q of the load by
the addition of a resistor in parallel or series with the load. A
value that draws one tenth of the current or DC voltage of
the load is usually sufficient.

For applications requiring a rapid controlled decay in the
solenoid current, such as fuel injector drivers, an external
zener and diode can be used as in Figure 3. The voltage
rating of the zener should be such that it breaks down before the output of the LM1950. The minimum output breakdown voltage of the IC output is rated at - 54V with respect
to the supply voltage.

Vee

For frequency stability of the switch, a 0.1 ,..F or larger output bypass capacitor is required.

0--.-----..-------,.----...,-,

Vee

ON,/Off
ON

""'"'ry
TL/H/11237-4

FIGURE 1

LM1950

LM1950

OUTPUT
OUTPUT - -....- - - ,
(PIN2)

LOAD

II

L

OUTPUT
OUTPUT - -...._ - - ,
(PIN2)

LOAD

lN4001

II

L

RL

TUHI11237 -6

TL/H/11237-5

FIGURE 3. Zener Clamp for Rapid
Controlled Current Decay

FIGURE 2. Diode Clamp
6-12

o

:;'

n

c

;:;

II I

c;:;;:l

,

en

J =tJ

, DY~i3

Dl

0'

OUTPUT

~

Co)

III

TUH/11237-9

II

OS6U..'

9-

Il)

Q)
9-

:IE
...I

r------------------------------------------------------------------------------------,

~National

~ Semiconductor

LM 1951 Solid State 1 Amp Switch
General Description

Features

The LM1951 is a high current, high voltage, high side (PNP)
switch with a built-in error detection circuit.

• 0.1 ,...A typical quiescent current (OFF state)
• 1 Amp output current guaranteed
• ± 85V transient protection
• Reverse voltage protection
• Negative output voltage clamp
• Error flag output
• Internal overvoltage shutdown
• Internal thermal shutdown
• Short circuit proof
• High speed switching (up to 50 kHz)
• Inductive or resistive loads
• Low ON resistance (1 (1 maximum)
• TTL, CMOS compatible input with hysteresis
• Plastic TO-220 5-lead package
• ESD protected
• 4.5V to 26V operation

The LM1951 is guaranteed to deliver 1 Amp output current
and is capable of withstanding up to ± 85V transients. The
built-in error detection provides an error flag output under
the following fault conditions: output short to ground or supply, open load, current limit, overvoltage or thermal shutdown. The LM1951 will drive all types of resistive or inductive loads. The output has a built-in negative voltage clamp
(~ - 30V) to provide a quick energy discharge path for
inductive loads. The LM1951 features TTL and CMOS compatible logic input with hysteresis. Switching times, both turn
on and turn off, are 2 ,...S (Cload < 0.005 ,...F). In addition, its
quiescent current in the OFF state is typically less than
0.1 ,...A at room temperature and less than 10 ,...A over the
entire operating temperature and voltage range.
The LM1951 features make it well suited for industrial and
automotive applications.

Typical Application Circuit and Connection Diagram
Vee =4.5V TO 26V
,Il0nF

ON

+5V., •.

.J

L2fF

O:"""""';:':"H-I

2kJl

ERROR 0 - -...FLAG

........
TUH/9133-1

VIN

o

Output

OFF
ON

TO-220, 5·Lead
4 ERROR FLAG
~ "'/'.
3 GROUND
2 OUTPUT (VOUT )
1 SUPPLY (Vee)
TL/H/9133-2

Front View
Order Number LM1951T
See NS Package Number T05A

6-14

r-

Absolute Maximum Ratings
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage
Operational Voltage
26Voc
Sustained Voltage
-40 VDe :<: Vce s: 85 Voc
Transient Voltage Protection
±85V
(T = 100 ms, 1 % Duty Cycle, Rs :<: 10n)
Pins 4, 5
26Voc

Power Dissipation (Note 1)
Load Inductance
Operating Temperature Range (TAl
Maximum Junction Temperature
Storage Temperature Range
Lead Temperature (Soldering, 10 sec.)
ESD Tolerance (Note 4):

Internally Limited
1H
-40'C to + 125'C
150'C
- 65'C to + 150'C
260'C
2000V

Electrical Characteristics
Vec = 12V, lout = 500 rnA, Cout = 0.001 ,..F, TA = 25'C unless otherwise specified
Parameter

Conditions

Typical

Supply Voltage, Vcc
Operational
Transient

Supply Current

100 mS,1 % Duty Cycle, Rcc:<: 10n

T =

Tested
Limit
(Note 2)

Design
Limit
(Note 3)

Units

4.5

Vmin

26

Vmax

-85

V

85

V

lout = 0 rnA, VON/OFF = 0.8V

0.1

10

lout = 250 rnA, VON/OA= = 2.0V

260

270

mAmax

lout = 600 rnA, VON/OA= = 2.0V

630

650

mAmax

lout = 1A, VON/OFF = 2.0V

1.06

1.2

Amax

Voltage Drop
(Vce - VOUT)

lout = 600 rnA, VONlOA= = 2.0V

400

600

mV max

lout = 1A, VON/OFF = 2.0V

0.7

1.0

Vmax

Short Circuit Current

VOUT = OV, VON/OFF = 2V

Input Threshold, Pin 5

4.5V

s:

Input Current, Pin 5

0.8V

s: VON/OFF s:

Output Clamp

lout

Delay
Time

Vcc

1.3

I TurnON
I TurnOFF

s: 26V
5.5V

Amin

2.5

Amax

2.0

2.0

1.2

0.8

0.8

-30

,..Amax

1.0

1.4

25

s: 600 rnA

100

Vmax
Vmin

50

,..Amax

10

,..Amin

-40

Vmin

-24

Vmax

1

3

,..smax

1

3

,..smax

Rise Time

1

3

,..smax

Fall Time

1

3

,..smax

t.J,ON
td,OFF

R'oad = 20n, Cload = 0.001 ,..F

Error Flag Characteristics:
Output Voltage

Error Condition, Pin 4 Low, Sinking 10 rnA

0.3

0.8

Vmax

Sink Current

Error Condition, Pin 4 = 0.3V

10

3

mAmin

Output Leakage Current

No Error, Pin 4 = 26V

0.01

1

,..Amax

Response Time

VLOGIC = 5V, RLOGIC = 2 kn, CLOGIC = O,..F

1

,..S

Note 1: Thermal resistance junction-to-case is 3°C/W. Thermal resistance case-to-ambient is 500C/W.

Note 2: Tested Limits are guaranteed and 100% production tested.
Note 3: Design Limits are guaranteed (but not 100% production tested) over the operating temperature and supply voltage range. These limits are not used to
calculate outgoing quality levels.
Note 4: Human body model. 100 pF discharged through a 1.5 kn resistor.

6·15

3:
....
CD
en
....

9-

~

9-

:!I

r-----------------------------------------------------------------------------------------------,
Typical Performance Characteristics
QuIescent Current

1

I

so

80

50

Vee II I2V
80 VoN/OFl' " 2V

70

Vee. 12V
VON/iii! • 2V

1

10- ',A-

I

40

eo
so

f\:

:E

~

,•• sooJ-- ~

50

40
50
20
10

Voltage Drop

QuIescent Current

100

~~

20

",
10

1,..00
~i"'"

o
o

0.10.20.50.40.5

o

o.e 0.7 o.e 0.11.0

-50 -25

OUTPUT CURRENT (A)

0.8

Vee" 12V
VON/OFl'i 2V

1 1
1

I 1

O. s

T

1

l

I

-50 -25

0

loalA 1/

0.5
0.2

to

II

OmA

O.

75

:E
...

~
~

!;

§

I

o
o

100 125

10

20

25

50

SUPPLY VOLTAOE(V)

ON/lWF Currant (PIn 5)
45

1.5

Ycc= t2y

40

I

55

TURN- N
lA

.....rr

50
25 I-TURN-

15

40
55
1
I
50
1/
25 1\ "401lJ.
VDM/OFl'" 2V
/
20
1/
15
1/
10
/
5
If
0
-5
-10
-10 -5 0 5 10 15 20 25 30 35 40

SUPPLY VOLTAOE (V)

ON/lWF Threshold (PIn 5)

1.5

,'"

HIgh Voltage BehavIor

o.e I
0.4 I
50

~

OUTPUT CURRENT (A)

0.8

0.2

- -t

20

rr

~

orr!

1,..00

o 0.1 D.2 U OA 0.5 O.S 0.7 0.8 O.t 1.0

1.0

25

.....

,

o

75 100 125

i-""'"

1.2

JUNCTION TEMPERATURE (DC)

1.2

12somA

VON/OFF" 2V

I.S

1 1
1 1

o

II

50

1.4

lo·,00mA
0.2

10

Short CIrcuIt Currant
1.8

IOl.ltaeOo mA
OA

25

0.5
OA

JUNCTION TEMPERATURE (DC)

,
J_

Voltage Drop

0

1.0
Ycc ·12V
O.t VON/OFl' " 2V
0.8
0.7
o,S

- .-ON_

ONIlWF Current (PIn 5)
45
40

I--

35

I--

50

Vee = 12V

JI
l{'"
/IJ..'

25

orr ..

20

5

5

10

0

N

5

o

1.0

o

10

15

20

1.0 1.1

25

SUPPLY VOLTAGE (V)

o
o

1.2 1.3 1.4 1.5 I.S 1.7

0.5

ON/Orl'VOLTAGE (V)

Output Voltage
ResIstIve Load

Output Voltage
InductIve Load
~

Vee -12V

\ 1\ =4011

I

1.0 1.5 2.0 2.5 3.0 3.5
ON/Orl'VOLTAGE (V)

!:j

20
10

0

~S-10

Vcc· ,2V
LOAD III 80 mH
-30
+4011 SERIES R
-40

~--20

I

~

S

12

16

200

TIME (1'.)

400

SOD

800

TIME (1'.)
TUH19133-3

6-16

!Ii....:

Error Flag Output Characteristics
Open Load Threshold
10

Open Load Threshold

Over Voltage Threshold
40

10

VCC=12V
9 VONIOri' = 2V

VONIOri' = 2V

9

CD
U1
Vee

=12Y

VONIOri' = 2V

~~

E

~~

....
=z
.... i:!

~

~

~

~

,,~

<'"
0<'>
~"

z<
~9
o

ro

10

i

.,..

o

15

20

25

o

-50 -25

SUPPLY VOLTAGE (V)

35

0

25

50

75

r---..
30
-50 -25

100 125

JUNCTION TEMPERATURE (OC)

0

25

50

75

100 125

JUNCTION TEMPERATURE (OC)

TlIH/9133-13

Truth Table
Fault Condition
Normal

Overvoltage

Thermal Shutdown

VOUT Short to GND

VOUT Short to Vsupply

Open Load

Current Limit

• L .. 0 ,;; VONtm'F ,;; O.8V

VON/OFF'

Vout

Error Flag

L

L

H

H

H

H

L

L

L

H

L

L

L

L

L

H

L

L

L

L

H

H

L

L
L

L

H

H

H

L

L

L

H

H

H

L

L

L

H

H

H

L

H .. 2V ,;; VONIlll'i' ,;; 26V

6-17

....

~
II)

en
~

::!

r------------------------------------------------------------------------------------------,
Typical Applications

....I

Vee

ON!OrF

=12V

0-,......-1
12, lA
1/2" NPT NORMALLY
CLOSED VALVE

ERROR
rLAG

TlIH/9133-4

FIGURE 1. Solenoid Actuated Valve

ON!OrF o-.::t-.......
3<1> 480V AC
60A RESISTIVE
OR 15 HP MOTOR
ERROR
nAG
TL/H/9133-5

FIGURE 2. 60A 3·Phase Mercury Displacement Relay
Vee = 12V

0-.----------.
2N4277'

43 kll
10

ON!OrF

nr

o-J .....-.::t-......

0-...+~---4-0 25A OUTPUT
lN1184
25A RECTlrlER
(NECESSARY mR
INDUCTIVE LOADS)

TlIH/9133-6

•Available from Germanium Power Devices, Andover, MA, Tel. (617) 475-5982

FIGURE 3. 25A Switch with Short Circuit Foldback

6·18

.-----------------------------------------------------------------------------, r
....
Typical Applications (Continued)
==
CD

....U1

Vee = 12V

100 nF

o-....~....-oOUTPUT
,I,1 nF

TLlH/9133-7

FIGURE 4. Latching Switch
Vee

=12V

HEATER

ERROR

FLAG
(OPEN HEATER DETECT)
TL/H/9133-8

FIGURE 5. Temperature Controller with Hysteresis
Vee = 12V

TLlH/9133-9

FIGURE 6. DC Motor Driver

6·19

Typical Applications (Continued)

TlIH/9133-10

FIGURE 7. Over-Voltage Crowbar
Vee = 12V

.:c10 nf

TlIH/9133-11
OperaUon

Switch Type

Empty

Normally Open

Fill

Normally Closed

FIGURE 8. Fluid Level Controller
Vec=12V

,Il0nf

#93 LAMP

TlIH/9133-12

FIGURE 9. Indicator Lamp Driver

6-20

,-----------------------------------------------------------------------------,
Application Hints
When inductive loads are turned OFF, they produce a negative voltage spike. The LM1951 contains a voltage clamp
that limits these spikes to approximately -30V, thus an external clamp is not necessary in most applications.

may be evident in a combination inductive/capacitive load,
or in an inductive load with supply decoupling capacitors in
the range of 100 nF to 1 J-LF. For fast rise and fall times and
minimum ringing with inductive loads, a supply decoupling
capacitor of 10 nF and an output capacitor of 1 nF is recommended. These should be located as close to the IC pins as
possible.
The error flag is an open collector output that pulls low under certain fault conditions. These errors include overvoltage (Vee> 26V), overcurrent (lOUT> 1.3A), undercurrent
(lOUT < 2 mAl, output short circuit to ground, output short
circuit to supply, and junction temperature greater than
150'C. By connecting a 2 kO resistor from the error flag
output to a 5V supply a logic output to a microprocessor is
provided.
The error flag can give seemingly false indications in a number of situations. Slewing large capacitive loads (>100 nF)
can drive the LM1951 into temporary current limit, producing a momentary error indication. Incandescent lamps and
DC motors require an inrush current that will also cause a
temporary current limit and error indication. Large inductive
loads (>50 mH) initially appear as open circuits, falsing the
error flag. The error flag pulses for about 1 J-Ls when any
load is turned ON since the output is initially at ground. In
microprocessor systems these false indications are easily
ignored in software. In discrete logic circuits utilizing a latch
at the error flag output, some filtering may be required.

Loads with an inductance of greater than 1H, driven to full
output current, may damage the clamp simply by exceeding
the power capabilities of the LM1951. An LM1951 can dissipate 25W continuous at 25'C ambient when mounted on a
large heatsink. If the load current is limited to 800 mA, the
sustained spike from an infinitely large inductance can be
handled. Sustained spikes produced by higher currents and
high inductances will exceed the 25W limit.
For inductances above 1H, care should be taken to see that
the output current does not exceed a value that could damage the clamp. While 800 mA is acceptable for the device
running at 25'C ambient on a heatsink, derate this current
for smaller heatsinks or higher ambient temperatures to limit
the junction temperature to 150'C. Alternatively, an external
clamp or resonating capacitor can be added to handle any
combination of load inductance, load current, and device
temperature. This is especially important if the output current is boosted, such as the application shown in Figure 3. A
peak power of 750W could be developed in the internal
clamp if an inductive load is switched without external
clamping.
Another case where the clamp's power capability may be
exceeded is when driving a solenoid. The inductance of a
solenoid is greatest when energized, with the plunger pulled
in. As the plunger is pulled out of the solenoid, the inductance goes down. Under certain conditions of high solenoid
inductance and fast mechanical time constants, the current
may actually Increase when the solenoid is turned OFF.
Since the energy stored in an inductor cannot change instantaneously, the current must increase to conserve energy when the inductance decreases. This condition is traced
by observing the load current with a current probe and storage oscilloscope.
Load capacitances larger than 1 nF will slow rise and fall
times. Inductive loads having a capacitive component larger
than 1 nF will also exhibit overshoot. Furthermore, ringing

An internal current sink (10 J-LA minimum) is connected to
the input, pin 5. If this pin is left open it is guaranteed to pull
low, switching the LM1951 OFF. This characteristic is important under certain fault conditions such as when the control line fails open cirucit.
Although the input threshold has hysteresis, the switch
points are derived from a very stable band-gap reference. In
many applications, such as Figures 5 and 7, the LM1951
input can replace an extenal reference and comparator.
The input (pin 5) is clamped at -0.7V and includes a series
resistance of approximately 30 kO. This pin tolerates negative inputs of up to 1 mA without affecting the performance
of the chip.

6-21

~

...3:
...
CD
U'I

C)
C)

;

r-------------------------------------------------------------------------------------,

~National

~ ~ Semiconductor
LMD18400
Quad High Side Driver
General Description

Features

The LMD18400 is a fully protected quad high side driver. It
contains four common-drain DMOS N-channel power
switches, each capable of switching a continuous 1 Amp
load (>3 Amps transient) to a common positive power supply. The switches are fully protected from excessive voltage,
current and temperature. An instantaneous power sensing
circuit calculates the product of the voltage across and the
current through each DMOS switch and limits the power to a
safe level. The device can be disabled to produce a "sleep"
condition reducing the supply current to less than 10 pA
Separate ON/OFF control of each switch is provided
through standard LSTLLlCMOS logic compatible inputs.

• Four independent outputs with >3A peak, 1A continuous current capability
II 1.3.0 maximum ON resistance over temperature
• True instantaneous power limit for each switch
• High survival voltage (60 Voc, 80V transient)
• Shorted load (to ground and supply) protection
• Overvoltage shutdown at Vee> 35V
• LS TTLICMOS compatible logic inputs and outputs
• < 10 p.A supply current in "sleep" mode
• -5V output clamp for discharging inductive loads
• Serial data interface for 11 diagnostic checks:
- Switch ON/OFF status
- Open or shorted load
- Operating temperature
- Excessive supply voltage
• Two direct-output error flags

A MICROWIRETM compatible serial data interface is built in
to provide extensive diagnostic information. This information
includes switch status readback, output load fault conditions
and thermal and overvoltage shutdown status. There are
also two direct-output error flags to provide an immediate
indication of a general system fault and an indication of excessive operating temperature.
The LMD18400 is packaged in a special power dissipating
leadframe that reduces the junction to case thermal resistance to approximately 20·C/W.

Applications
•
•
•
•
•

Relay and solenoid drivers
High impedance automotive fuel injector drivers
Lamp drivers
Power supply switching
Motor drivers

Typical Application

10

Switch
Select

11

Inputs

12

Connection Diagram

In 1
In 2

Ccp

In 3

I.

In'

Output 1

Io.o

11'F

10kQ
+5V

13
Error

Chip Select
0
0

....
co
C

Error

'"

Out 1

Thermal

Dale. Output
Out 3

Input 1

18

Input 2

CS
Clock
Diagnostic
Data Output

Thermal Shutdown

16

Ground

C

15

Ground

..J

1•

C charge pump (Ccp)

13

Error

'"

Clock

Out 2

..J

Thermal
Shutdown

Output 3

....
co

Ground

Out 4-

19

10

Output 4

18
0
0

Ground

19

17

Enable

Enable

Enable

Vee

Output 2

12

Input 4-

11

Input 3

TUH/11026-2

Order Number LMD18400N
See NS Package Number N20A

Data Output

TUH/11026-1

6-22

r

Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Survival Voltage (Pin 20)
Transient (t = 10 ms)
Continuous

80V
-0.5Vto +SOV

Output Transient Current (Each Switch)

SA

Output Steady State Current (Each Switch)

1A

Logic Input Voltage (Pins 4,7)

16V

ESD Susceptibility (Note 2)

2000V

Power Dissipation (Note 3)

5W
Internally Limited
150'C
- 65"C to + 150'C

Junction Temperature (TJMax)
Storage Temperature Range

3.75A

Output Transient Current (Total, All Switches)
Logic Input Voltage (Pins 3, 9, 10, 11, 12)

Error Flag Voltage

Lead Temperature (Soldering, 10 Sec.)

Operating Ratings

-0.3V to + 16V

(Note 1)

Ambient Temperature Range (TAl

-0.3Vto +6V

+ 260'C

-40'C to + 125'C

Supply Voltage Range

6Vt028V

Electrical Characteristics Vee = 12V, cep = 0.Q1 ,..Fd, unless otherwise indicated. Boldface limits apply
over the entire operating temperature range, - 40'C ,,; T A ,,; + 125'C, all other limits are for T A = TJ = + 25'C.
Parameter

Conditions

Typical
(Note 4)

Limit
(Note 5)

Units
(Limit)

0.04
7.5

10
15

p.A (Max)
mA(Max)

DC CHARACTERISTICS
Supply Current

Enable Input = OV
Enable Input = 5V, Inputs = OV
Enable Input = 5V, Inputs = 5V
Open Loads

7.5

15

mA(Max)

Output Leakage

Enable Input = OV, Inputs = OV
(Pins 1,2,18,19)

0.Q1

10

,..A(Max)

RdsON

lOUT = 1A, (Note 6)

0.8

1.3

n(Max)

Short Circuit Current

Vee = 12V, (Note 6)
Vee = 6V, (Note 6)
Vee = 28V, (Note 6)

1.2
2.4
0.6

0.8

A (Min)
A
A

Maximum Output Current

Vee - Va = 4V, (Note 6)

3.75

Load Error Threshold Voltage

Pins 1, 2,18,19

4.1

V

Open Load Detection Current

Pins 1, 2, 18, 19

150

p.A

Negative Clamp Output Voltage

10 = 1A, (Note 6)

-5

V

Overvoltage Shutdown Threshold

35

Overvoltage Shutdown Hysteresis

0.75

A

40

V (Max)

10

p.A(Max)

V

Error Output Leakage Current

VPin13 = 12V

0.001

Thermal Warning Temperature

VPin 13

< 0.8V
< 0.8V

145

·C

170

·C

Thermal Shutdown Temperature

VPin 17

.'

6-23

:s:
c
....
co
~

Q
Q

Electrical Characteristics Vee = 12V, COP
over the entire operating temperature range, -40"C S; TA S;
Parameter

= 0,01

,.F, unless otherwise Indicated. Boldface limits apply

+ 12SoC, all other limits are for TA = TJ = + 2SoC. (Continuad)

Conditions

Typical
(Note 4)

Limit
(Note 5)

Units
(Limit)

5

10

,.s (Max)

7

15

,.s (Max)

O.S

2

O.lS

1

,.s (Max)

AC CHARACTERISTICS

= SV,

Switch Turn-On Delay
(IeI(ON»

Enable (Pin 3)
lOUT = lA

Switch Turn-On Rise
Time (!oN)

lOUT

Switch Turn-Off Delay
(IeIOFF)

Enable (Pin 3)
lOUT = lA

Switch Turn-Off Fall
Time (!oFF)

lOUT

Enable Time (tEN)

Measurad with Switch 1,
Pin 9 = SV

30

50

/los (Max)

Error Reporting Delay
(tError)

Enable (Pin 3) = SV,
Switch 1 Load Opened

7S

150

,.s (Max)

Data Setup Time (tos)

CL

200

SOO

ns(Min)

TRI-STATE4D Control (t1H' !oH)

Pin 8, Hi-Z Enable Time

= lA
= SV,

= lA

= 30pF

Data Clock Frequency

2
3

,.s (Max)

,.s
1

MHz (Max)

DIGITAL CHARACTERISTICS
Logic "1" Input Voltage

Pins 3, 4, 7, 9,10,11,12

2.0

V (Min)

Logic "0" Input Voltage

Pins3,4, 7,9,10,11,12

0.8

V (Max)

Logic "1" Input Current

Pins 4, 7

0.001

1

Logic "0" Input Current

Pins 4, 7

-0.001

-1

/loA (Max)
/loA (Max)

TRI-STATE Output Current

Pin 8, Pin 4
Pin8 = OV

O.OS
-O.OS

10
-10

/loA (Max)
/loA (Max)
/loA (Max)

= SV

= 2.4V

Enable Input Current

Pin 3

Channel Input Resistance

Pins 9, 10, 11, 12

Error Output Sink Current

Pin 13

Logic "1" Output Voltage

PlnB
lOUT = -380/loA
lOUT = -10 /loA
lOUT = -10/loA

= 0.8V

logic "0" Output Voltage

PlnB
lOUT = 100 /loA

Thermal Shutdown Output
Source Current

Pin 17 = 2.4V

Thermal Shutdown Output
Sink Current

Pin 17

= O.BV

6-24

12

25

7S

25

kO(Min)

4

i.e

mA(Min)

4.4
S.1

2.4
4.5
5.5

V (Min)
V (Min)
V (Max)

0.4

.V(Max)

S

3

/loA (Min)

360

2S0

,.A (Min)

r-

;:

Electrical Characteristics Notes
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is

intended to be functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics.

Note 2: Human body model; 100 pF discharge through a 1.5 kn resistor. All pins except pins 8 and 13 which are protected to 1000V and pins 1, 2, 18 and 19 which
are protected to 500V.
Note 3: The maximum power dissipation is a function of TJMax' 8JA. and TA and is limited by thermal shutdown. The maximum allowable power dissipation at any
ambient temperature is Po = (TJMax - TtJI8JA. If this dissipation is exceeded, the die temperature will rise above 150'C and the device will eventually go into

thermal shutdown. For the LMD18400 the junction-ta-ambient thermal resistance, 8JA. is arrc/w. With sufficient heatsinking the maximum continuous power
dissipation for the package will be, IOCMax2 X RON(Max) X 4 switches (1 A2 X 1.3n X 4 = 5.2W).

Note 4: Typical values are at TJ

=

+ 25'C and represent the most likely parametric norm.

Note 5: All limits are 100 0/0 production tested at + 25°C. Limits at temperature extremes are guaranteed through correlation and accepted Statistical Quality
Control (SOC) methods.

Note 6: Pulse Testing techniques used. Pulse width is

< 5 ms with a duty cycle < 1 %.

Timing Specification Definitions
Switching Turn ON/OFF
Enable

Enable Turn-ON

= 5V

Channell Input

= 5V

+5V

+5V

Enable
Input

Channel
Input

--,/---50%

OV

OV

Your

Your
Switch 1
Output

Switch
Output

OV _ _ _ _II

10%

OV--""

TL/H/l1026-4

TL/H/ll026-3

Error Reporting Delay

Data Setup Time

Channel 1 output open circuited.

+5V

+5V
Channell
Input

Chip Select
......l~--50%

OV

OV

+5V

+5V
Error Flag
Output

Clock

;:---50%

OV

OV

TL/H/ll026-6

TLlH/ll026-5

6-25

C
....
CO
~

o
o

Typical Performance Characteristics
For all curves, Vee = 12V, Temperature is the junction temperature unless otherwise noted.

Switch ON Resistance
vs Temperature
13

z

V

V

6

1/

1.0

....
.3

V

0.9

Jl

1/

o.s

5

~

40

0

80

120

0

..... -~

1

--

I

~-

~

1S0oe

!;<

~

1

40

80

120

160

'~"

4Oi-

9

1A

8-

]

20

'"

!i:

i

..... f0

40

80

120

160

!!5

7

1.8
1.6

1A

....3
~

'"

;:

~

;

V

~

I--'~

40
-40

0

40

f-

80

TEMPERATURE (oe)

120

160

80

120

160

120

160

1 1.1
'LOAO = lA

1.4
1.2
1.0
0.8
0.6
Q.4

0

40

80

120

-40

160

0

40

80

TEMPERATURE (oe)

Error Output Voltage
vs Sink Current
3.0

!J

_r-

o:l

V

80

40

0

Turn OFF Time
vs Temperature

2.0

§!

1/

100

. . . . r-

3,4

Enable Threshold Voltage
vs Temperature

~

V

160

TEMPERATURE (oe)

1.6

120

120

3.6

3.2
-40

8

..... ~ ~-

..........

80

.......~

£

140

60

ill
6

40

....... :--,

TEMPERATURE (oe)

(Pins 9. 10. 11. 12)

~

3.6

~

...

4
-40

160

~

5

ILOAD

6

Switch Select Logic Input
Resistance vs Temperature

tl

!;l

I II
=

TEMPERATURE (oe)

!

4.0

~

7

5

,.....

0
-40

~

;:

Tum ON Delay Time
vs Temperature

30

10

0

NEGATIVE CLAMP VOLTAGE

I II
=

ILOAD

/

fl
~

I'r-."
..... ~

I I

1

~ 4.2~

Ih
3

Tum ON Rise Time
vs Temperature
50

Free Air

4.6

'/

j

]"

'-

£ «

1/

TEMPERATURE (oe)

...

II.

I

2

,,

I

Error Sense Threshold
Voltage vs Temperature

-ZOoc

3

0
0

2 -

0
-40

160

1
1

25°C

4

~

0
-40

3......

AM81ENT TEMPERATURE (oe)

5

3:

0.5

.3
!i:

120

In11nlte

Clamp Characteristics
vs Temperature

2

Jl

80

40

OJ!.:\ f-\; ~~~~k

=330 C!W"

TEMPERATURE (oe)

Short Circuit Current
vs Temperature

3:

~

~

j
~

TEMPERATURE (OC)

1.5

~

~

3

0
-40

160

5

~

4

1

0.6

~
z

2

I.--'V

0.7

Enable = OV
Outputs grounded
Includes output
Inksg. currant.

7

1.1

0

,}

6

8

1.2

:s

Maximum Power
Dissipation vs
Ambient Temperature

"Sleep" Mode Supply Current
vs Temperature

£

1.5

v1v

I;

,;'

/

25°C

VV

1.0

I~V
1.4
~

0
0

40

80

TEMPERATURE (OC)

120

160

0

2

4

6

8

10

SINK CURRENT (rnA)

TL/H/l,026-7

6·26

r-

:s::
c
....

Functional Block Diagram

CD

OUTPUT 1

1

1------------.

OUTPUT 2

2

1---------.....,

.a:o.
o
o

r--+--+---H>---I---+-----I18

OUTPUT 3

TIiE'ii'UAL
SHUTOOWN

-I:1!]

GROUNO~

CLOCK

7

GROUND

1--+-+11>

30}'s OELAY

-=

-=

TLlH111026-8

Truth Table
Enable
Input
(Pin 3)

Chip Select
Input
(Pin 4)

Switch Control
Input
(Pins 8, 9, 10, 11)

Error
Output
(Pin 13)

ThermalSD
Output
(Pin 17)

0

X

X

0

0

X

0

0

< 10,..A

Selected Switch is ON, Normal Operation
0

X

X

"Sleep" Mode, ISu I

Selected Switch is OFF

X
X

Conditions

0

Switch is OFF but:
a. Load is Open Circuited, or
b. Load is Shorted to Vee, or
c. TJ > + 145'C, or
d. Vee> +35V

0

Switch is ON, but;
a. Load is Shorted to Ground, or
b. Switch is in Power Limit, or
c. TJ > + 145'C, or
d. Vee> + 35V and Switch is Actually OFF

1

0

0

TJ > + 17O'C, All Switches are OFF

X

X

X

Data Output Pin is TRI-STATE

X

X

X

Data Output Pin is Enabled and Ready to
Output Diagnostic Information

6-27

II

gr-------------------------------------------------------------------~

'III'

Applications Information

C

BASIC OPERATION
High-side drivers are used extensively in automotive and
industrial applications to switch power to ground referred
loads. The major advantage of using high-side drive, as opposed to low-side drive, is to protect the load from being
energized in the event that the load drive wire is inadvertently shorted to ground as shown in Figure 1. A high-side
driver can sense a shorted condition and open the power
switch to disable the load and eliminate the excessive current drain on the power supply. The LMD18400 can control
and protect up to four separate ground referenced loads.

co

~

The LMD18400 can be continually connected to a live power source, a car battery for example, while drawing less than
10 fLA from the power source when put into a "sleep" condition. This "sleep" mode is enacted by taking the Enable
Input (pin 3) low. During this mode the supply current for the
device is typically only 0.04 ",A. Special low current consumption standby circuitry is used to hold the DMOS
switches OFF to eliminate the possibility of supply voltage
transients from turning on any of the loads (a common problem with MOS power devices). When in the "sleep" mode,
all diagnostic and logic circuitry is inactive. When the Enable
Input is taken to a logic 1, the switches become "armed"
and ready to respond to their control input aiter a short,
30 ",s, enable delay time. This delay interval prevents the
switches from transient turn-on. Figure 2 shows the switch
control logic.

High Side Drive

T~
Short can be . e n . O d 1 Q ,
and the swRch can be
opened
Load

...L

-=

Output

TL/H/11026-9

Low SIde Drive
Enable

- -......--ov+

c~~~;~ 0-----1
Load

:

...L

ShT:t~:wa~ 0---...1

o~~~=:!~ 0 - - - - - '

Short will onOl\lIz•
th.load

TUH/11026-11

FIGURE 2. Control Logic for Each Power Switch
Each DMOS switch is turned ON when its gate is driven
approximately 3.5V more positive than its source voltage.
Because the source of the switch is the output terminal to
the load it can be taken to a voltage very near the Vee
supply potential. To ensure that there is sufficient voltage
available to drive the gates of the DMOS device a charge
pump circuit is built in. This circuit is controlled by an internal
300 kHz oscillator and using an external 10 nF capacitor
connected from pin 14 to ground generates a voltage that is
approximately 20V greater than the Vee supply voltage.
This provides sufficient gate voltage drive for each of the
switches which is applied under command of standard 5V
logic input levels.

TUH/11026-10

FIGURE 1. High-Side vs Low-Side Drive
The LMD18400 combines low voltage CMOS logic control
circuitry with a high voltage DMOS process. Each DMOS
power switch has an individual ON/OFF control input. When
commanded ON, the output of the switch will connect the
load to the Vee supply through a maximum resistance of
1.3n (the ON resistance of the DMOS switch). The voltage
applied to the load will depend upon the load current and
the designed current capability of the LMD18400. When a
switch is commanded OFF, the load will be disconnected
from the supply except for a small leakage current of typically less than 0.D1 ",A.

"'S

The turn-on time for each switch is approximately 12
when driving a lA load current. This relatively slow switching time is beneficial in minimizing electromagnetic interference (EMI) related problems created from switching high
current levels.

6-28

Applications Information

Ii:

(Continued)

PROTECTION CIRCUITRY
The LMD18400 has extensive protection circuitry built in.
With any power device, protection against excessive voltage, current and temperature conditions is essential. To
achieve a "fail-safe" system implementation, the loads are
deactivated automatically by the LMD18400 in the event of
any detected overvoltage or over-temperature fault conditions.

The LMD18400 has been designed to drive all types of
loads. When driving a ground referenced inductive load
such as a relay or solenoid, the voltage across the load will
reverse in polarity as the field in the inductor collapses when
the power switch is turned OFF. This will pull the output pin
of the LMD18400 below ground. This negative transient
voltage is clamped at approximately -5V to protect the IC.
This clamping action is not done with diodes but rather the
power DMOS switch turning back on momentarily to conduct the inductor current as it de-energizes as shown in
Figure 4.

Voltage Protection
The Vee supply can range from -0.5V to + 60 Voe without
any damage to the LMD18400. The CMOS logic circuitry is
biased from an internal 5.1 V regulator which protects these
lower voltage transistors from the higher Vee potentials. In
order to protect the loads connected to the switch outputs
however, an overvoltage shutdown circuit is employed.
Should the Vee potential exceed 35V all of the switches are
turned OFF thereby disconnecting the loads. This 35V
threshold has 750 mV of hysteresis to prevent potential oscillations.

- - -....-oVCC

I-

:=~

I""""

.... OV

+

!

Switch comes 'on'
to conduct load
current

±r-

VOUT
OV--5V

IL

TL/H/ll026-13

FIGURE 4, Turn-OFF Conditions with an Inductive Load
When the output inductance produces a negative voltage,
the gate of the DMOS transistor is clamped at OV. At
-3.5V, the source of the power device is less than the gate
by enough to cause the switch to turn ON again. During this
negative tranSient condition the power limiting circuitry to
protect the switch is disabled due to the gate being held at
OV. The maximum current during this clamping interval,
which is equal to the steady state ON current through the
inductor, should be kept less than 1A. Another concern during this interval has to do with the size of an inductive load
and the amount of time required to de-energize it. With larger Inductors It may be possible for the additional power dissipation to cause the die temperaure to exceed the thermal
shutdown limit. If this occurs all of the other switches will
turn OFF momentarily (see section on Thermal Management).

Over/Under
Voltage Shutdown

r-...

Vee
OV~~+-+*+*~~~~~~

40V

3.5~ I VOUT

Additionally, there is an undervoltage lockout feature built
in. With Vee less than 5V it becomes uncertain whether the
logic circuitry can hold the switches in their commanded
state. To avoid this uncertainty, all of the switches are
turned OFF when Vee drops below approximately 5V.
Figure 3 illustrates the shutoff of an output during a OV to
80V Vee supply transient.

sov

~~
~..

I-t-t-t-t-t--c:+-+-+-+--l

r:--.._

Vert: 20VIDIV Horl.: 10 ml/DIV

Power Limiting
The LMD18400 utilizes a true Instantaneous power limit circuit rather than simple current limiting to protect each
switch. This provides a higher transient current capability
while still maintaining a safe power dissipation level. The
power dissipation in each switch (the product of the Drain-to
Source voltage and the output current, Vds X lOUT) is con-

TL/H/ll026-12

FIGURE 3. Overvoltage/Undervoltage Shutdown

6-29

c
.....
0)

".,

CI
CI

o
o

•....
CO

c

:::i
....I

Applications Information (Continued)
tinually monitored and limited to 15W by varying the gate
voltage and therefore the ON resistance of the switch. Basically the ON resistance will be as low as possible until 15W
is being disSipated. To maintain 15W, the ON resistance
increases to reduce the load current. This results in a decrease of the output voltage. For resistive loads, the output
voltage when in power limit will be:
VOUT (in Power Limit) = Vee -

This dynamic current limiting of the switches is beneficial
when driving lamp and large capacitive loads. Lamps require a large inrush current, on the order of 10 times the
normal operating current, when first switched on with a cold
filament. The LMD18400 will limit this initial current to the
level where 15W is dissipated in the switch. As the filament
warms up the voltage across the lamp increases thereby
decreasing the voltage across the switch which permits
more current to fully light the lamp. With limited inrush curent the lifetime of a lamp load is increased significantly.
Figure 6 illustrates the soft turn-on of a lamp load.
The same principle of increasing output current as the voltage across the load increases-allows large capacitive loads
to be charged more quickly by an LMD18400 driver than as
opposed to a driver with a fixed 1A current limit protection
scheme. Rgure 7 shows the output response while driving a
large capacitive load.

Ncr;

This provides a maximum transient current and drain-tosource voltage characteristic as shown in Figure 5.
4

3

3:

5

.S>

2

/"\ '\
I/" '-<:

Thermal Protection
The die temperature of the LMD18400 is continually monitored. Should any conditions cause the die temperature to
rise to + 170"C, all of the power switches are turned OFF
automatically to reduce the power dissipation. It is important
to realize that the thermal shutdown affects all four of the
switches together. That is, if just one switch load is enough
to heat the die to the thermal shutdown threshold, all of the
other switches, regardless of their power dissipation conditions, will be switched OFF. All of the switches will be re-enabled when the die temperature has cooled to approximately + 160"C. Until the high temperature forcing conditions
have been removed the switches will cycle ON and OFF
thus maintaining an average die temperature of + 165"C.
The LMD18400 will signal that excessive temperatures exist
through several diagnostic output signals (see Diagnostics).

15 Walt Power LImit

-

On Resistance
Current LImit

I
5

10

15

r-20

25

30

SWITCH DRAIN - SOURCE VOLTAGE (V)
TL/H/11026-14

FIGURE 5. Maximum Output Current with
Instantaneous Power Limiting
Driving a Lamp
Vee

=12V

Driving a Large
Capacitive Load

r- 12V, 2A Lamp

=
=

Vee 12V
CLOAD 47OOl'Fd

[I
,...~

Your

~

OV

I-

!I

I
VOUT

Vert: 5V/DIV Horiz: 100 mS/DIY

OV

V

TLlH/11026-15

FIGURE 6. Soft Turn-On of a Lamp Load

Vert: 5V/DIY Hortz: 20 ms/DIV

The steady state current to the load is limited by the package power dissipation, ambient temperature and the ON reo
sistance of the switch which has a positive temperature coefficient as shown in the Typical Performance Characteris·
tics.

TLlH/11026-16

FIGURE 7. Driving a Large Capacitive Load

6-30

Applications Information

(Continued)

DIAGNOSTICS
The LMD18400 has extensive circuit diagnostic information
reporting capability. Use of this information can produce
systems with intelligent feedback of switch status as well as
load fault conditions for troubelshooting purposes. All of the
diagnostic information is contained in an 11-bit word. This
data can be clocked out of the LMD18400 in a serial fashion
as shown in Figure 8. The shift register is parallel loaded
with the diagnostic data whenever the Chip Select Input is
at a Logic 1 and changes to the serial shift mode when Chip
Select is taken to a Logic O. The Data Output line (pin 8) is
biased internally from a 5.1 V regulator which sets the Logic
1 output voltage. This pin has low current sourcing capability
so any load on this pin will reduce the Logic 1 output level
which is guaranteed to be at least 2.4V with a 360 p.A load.

tion, one for each channel in succession (see Load Error
Detection).
Bits 5 through 8 provide a readback of the commanded
ON/OFF status of each switch.
A unique feature of the LMD18400 is that it provides an
early warning of excessive operating temperature. Should
the die temperature exceed + 145°C, bit 9 will be set to a
Logic O. Acting on this information a system can be programmed to take corrective action, shutting OFF specific
loads perhaps, while the LMD18400 is still operating normally (not yet in thermal shutdown). If this early warning is
ignored and the device continues to rise in temperature, the
thermal shutdown circuitry will come into action at a die temperature of + 17O"C. Should this occur bit 10 of the diagnostic data stream will be set to a Logic 0 indicating that the
device is in thermal shutdown and all of the outputs have
been shut OFF.

The data interface is MICROWIRE compatible in that data is
clocked out of the LMD18400 on the falling edge of the
clock, to be clocked into the controlling microprocessor on
the rising edge. Any number of devices can share a common data output line because the data output pin is held in a
high impedance (TRI-STATE) condition until the device is
selected by taking its Chip Select Input low. Following Chip
Select going low there is a short data setup time interval
(500 ns Min) required. This is necessary to allow the first
data bit of information to be established on the data output
line prior to the first rising clock edge which will input the
data bit into the controller. When all 11 bits of diagnostic
data have been shifted out the data output goes to a Logic 1
level until the Chip Select line is returned high.
Figure 8 also indicates the significance of the diagnostic
data bits. The first 4 bits indicate an output load error condi-

CHIPsaEcr

The final data bit, bit 11, indicates an overvoltage condition
on the Vee supply (Vee is greater than 35V) and again indicates that all of the drivers are OFF.
The diagnostic data can be read periodically by a controller
or only in the event of a general system error indication to
determine the cause of any system problem. This general
indication of a fault is provided by an Error Flag output (pin
13). This pin goes low whenever any type of error is detected. There is a built-in delay of approximately 75 p.s from the
time an error is detected until pin 13 is taken low. This is to
help mask short duration error conditions such as may be
caused by driving highly capacitive loads (>2 p.F). A lamp
load may generate a shorted load error for several hundred
milliseconds as it turns on which should be ignored.

-----,~:~------------------------------------------------------------~r---:

:-- setup time required

CLOCK

DATA OUTPUT

Tri-State

BIT

#
CH1

2

3

4

5

6

7

8

CH2

CH3

CH4

CHI

CH2

CH3

CH4

~--------v~--------~
ERROR STATUS

9

10

11

'---------v~--------~
ON/OFF STATUS

LOAD OK

SWITCH OFF

LOAD ERROR

SWITCH ON
TUH/11026-17

FIGURE 8. Serial Diagnostic Data Assignmento

6-31

Applications I nformation (Continued)
The Error Flag output pin is an open drain transistor which
requires a pull-up resistor to a positive voltage of up to 16V.
Typically this pull-up is to the same 5V supply which is biasing the Enable input and any other external logic circuitry.
The Error Flag pins of several LMD18400 packages can be
connected together with just one pull-up resistor to provide
an all-encompassing general system error indication. Upon
detection of an error, each device could then be polled for
diagnostic information to determine the source of the fault
condition.
A second direct output error flag is for an indication of Thermal Shutdown (pin 17). This active low flag provides an immediate indication that the die temperature has reached
+ 170·C and that the drive to all four switches has been
removed. This output is pulled up to the internal 5.1 V logic
regulator through a small (5 /LA) current source so use of a
buffer on this pin is recommended.
t5.2V Bias

LOAD ERROR DETECTION
An important feature of the LMD18400 is the ability to detect open or shorted load connections. Figure 10 illustrates
the detection circuit used with each of the drivers.

SDk

4.1V

+5V

Aeference -

TL/H/11D26-19

FIGURE 10. Detection Circuitry
for Open/Shorted Loads
A voltage comparator monitors the voltage to the load and
compares it to a fixed 4.1 V reference level. When a switch is
OFF, the ground referenced load should have no voltage
across it. Under this condition, an internal 50 kO resistor
connected to Vee will provide a small amount of current to
the load. If the load resistance is large enough to create a
voltage greater than 4.1V an Open Load Error will be indicated for that switch. The maximum load resistance that will
not generate an Open Load Error when a switch Is OFF can
be found by:

J
Open Collector
Inverter or Buffer

LND1B4DD
TL/H/11026-16

FIGURE 9. Thermal Shutdown Flag and Shutdown Input
A useful feature of pin 17 is that it can also be used as a
shutdown input. Driving this pin low immediately switches all
of the drivers OFF, just the same as if thermal shutdown
temperatures has been reached, yet all of the control logic
and diagnostic circuits remain active. This is useful in designing "fail-safe" systems where the loads can be disabled
under any sort of externally detected system fault condition.
The diagnostic logic however does not distinguish between
normal thermal shutdown or the fact that pin 17 has been
driven low. As such, various switch errors and an over-temperature indication will be reported In the diagnostic data
stream.
Figure 9 Illustrates the use of pin 17 as both an output thermal shutdown flag and as an input to shut down only the
switches. Directly tying pin 17 to + 5V will prevent the internal thermal shutdown circuitry from disabling the switches.
For reliability purposes however this is not recommended as
there will then be no limit to the maximum die temperature.
Refer to the Truth Table for a summary of the action of
these direct-output error flags.

RMax = V 4.1 V 6V X 50 kO; for no Open Load Indication
ee - 4.
To make this Open Load Error threshold more sensitive, an
external pull-up resistor can be added from the output to the
Vee supply.
Also when a switch is commanded OFF, should the load be
shorted to the Vee supply, this same circuitry will again indicate an error.
When a switch is commanded ON, the load is expected to
have a voltage across it that approaches the Vee potential.
If the output voltage is less than the 4.1 V threshold an error
will again be reported, indicating that the load Is either shorted to ground or that the driver is in power limit and not able
to pull the output voltage any closer to Vee. The minimum
load resistance that will not generate a Shorted Load Error
when a switch is ON can be found by:
4.1V (Vee - 4.1V)
RMln =
15W
; for no Shorted Load Error

6-32

Applications Information

(Continued)

Figure 11 indicates the range of load resistance for normal
operation, open load, and shorted load or power limit indication.
40k
30k

5
""u
:z
......
iii
...
...""

I

~

\

20k

I
I
I
Oetected as an
~pen Load
_L
I

10k

If"""

CI"I

1k

Normal Opera.tion

Q

'"

Careful calculation of the worst case total power dissipation
required at any point in time, together with providing sufficient heatsinking will prevent this from occurring.
The LMD18400 is packaged with a special leadframe that
helps dissipate heat through the two ground pins on each
side of the package. The thermal resistance from junctionto-case (8Jcl for this package is approximately 20·C/W.
The thermal resistance from junction-to-ambient (8JAl, without any heatsinking, is approximately 60·C/W. Figure 12 illustrates how the copper foil of a printed circuit board can
be designed to provide heatsinking and reduce the overall
junction-to-ambient thermal resistance.
The power dissipation in each switch is equal to:

10

....I

5
0

~
10

~

15

! .-+--

20

Oetected as a Shorted Load

25

30

35

40

r45

Po (Each Switch) = ILoad 2 X RON

(Vee - VOUT)2

or

RON
where RON is the ON resistance of the switch (1.30 maximum). These equations hold true until the power dissipation
reaches the maximum limit of 15W. With resistive loads, the
15W power limit threshold will be reached when:
Vee2
RL s: 60W

50

Vee (V)
TLlH/ll026-20

FIGURE 11. Load Resistance Detected as Errors
THERMAL MANAGEMENT

Inductive loads will create additional power dissipation when
switched OFF. Figure 13 shows the idealized voltage and
current waveforms for an inductive load.

It is particularly important to consider the total amount of
power being dissipated by all four switches in the
LMD18400 at all times. Any combination of the switches
driving loads will cause an increase in the die temperature.
Should the die temperature reach the thermal shutdown
threshold of + 170·C, all of the switches will be disabled.

Maximum Power Dissipated
and Junction to Ambient
Thermal Resistance vs Size

I
I ~ '!.'loC") ~ ~
I---

C-.

I

\'"\0"\

~~~ .....

;;..........
.....
.......
.....

"

........

-'JA

I-- I-~ I-

1.0

o
o

80

20

10

20

30

40

50

L SIZE (mm)
TL/H111026-22
TLlH/ll026-21

FIGURE 12. Recommended PC Board Layout to Reduce the Thermal Resistance from Junction-to-Ambient

6-33

ri:
c
......

co

-1=00
CI
CI

Applications Information (Continued)

+5V
Switch OV

Control

power limit protection. If the inductor is too large, the time
interval may be long enough to heat the die temperature to
+ 170'C thereby shutting OFF all other loads on the package.

n..

r::-1
I
--1 ON ~
I- ton -I- tolf -I

The total average power dissipation during a full ON/OFF
switching cycle of an inductive load will be:
PO(tot)

r-\.

Ipeek

ILOAD OA - - . /

~lamp

Your

OV ---I

-5V

I

Lr-J
TUH111026-23

FIGURE 13. Switching an Inductive Load
When switched ON, the worst case power dissipation is:
PO(ON)

= Ipeak2 x

RON; where IPeak

Vcc
= :::R-=-::-

+ 5V)
2

+ 5V)]

1

toN

+ toFF

30
10
'0'

.;
'":::I!

x IPeak

1=

\

3

l"0.3

r--....

0.1

for the time interval, tClamp, which is the time required for
the inductor current to fall to zero;
tClamp =

10

100

ON + Rs
The steady-state ON current of the inductor should be kept
less than 1A per power switch.
The additional power dissipation during turn-off, as the inductor is de-energized and the voltage across the inductor
is clamped to -5V, can be found by:
P
(Vcc
O(OFF) =

IPeak2L (Vcc

Due to the common cut-off of all loads forced by thermal
shutdown, the thermal time constants of the package become a concern. Figure 14 provides an indication of the
time it takes to heat the die to thermal shutdown with a step
increase in package power dissipation from an initial junction temperature of + 25'C. This data was measured using
a PC board layout providing a thermal resistance from junction to ambient of approximately 35'C/W. Less heatsinking
will, of course, result in faster thermal shutdown of the power switches.

"------

H
Vee

= [ l~eak2 RON toN +

r-- ........

0.03

o

IPeak xL

-sv--

o

10

20

30

40

50

60

TOTAL PACKAGE POWER
DISSIPATION (W)

The size of the inductor will determine the time duration for
this additional power dissipation interval. Even though the
peak current is kept less than 1A, the switch during this
interval will see a voltage across it of VCC + 5V with no

TLlHlll026-24

FIGURE 14. Approximate time required for the die to
reach the 170'C thermal shutdown point from 25'C for
different total package power dissipation levels.

6-34

Applications
ON/OFF Switching of multiple voltage regulated circuit loads. Reset flag feedback from the LM2926
as shown connected to Output 4 can make the LMD18400 act as an electronic fuse for load faults.
vee = 1210 28V

Load Circuit Select Inputs

ON

~

20

+1DV Circuit

10

+BV Circuit

11

+5V Circuit

12

+5V Circuit

Enable

In 1
In 2
In 3

I

In 4

o 10
lA
Load

Enable

10 kll

0
0

13

..q-

Error

+5V

Dull

co

Error

C

::::;

Oul 2

o 10
lA
Load

...J

Thermal

Thermal

Shutdown

oul 3

18

CS
Clock
Diagnostic
Oala oulpul

oul 4

19

Oala oulpul

o 10
lA
Load

16

o 10
0.5A
L08d

Delayed Reset

Error

rcla~g~_ _ _,

TL/H/ll026-25

Unipolar Drive for a 4-Phase Stepper Motor

20
10

Winding
Drive
Inputs

11
12

Enable

In 1
In 2

Ccp

In3

14

In4

I

o•01 J.1F

Enable

lokll
+5V

13
Error

0
0

Dull
Stepper Wotor
(IA Max

..qCO

Q

Error

::::;
...J

Thermal
Shutdown

Thermal

per winding)

r\----.

oul2

Oul3

18

CS
Clock
Diagnostic
oala oulpul

Oul4

19

Data Output

5

TL/H/ll026-26

6-35

§co
....
:i

Applications (Continued)

Q

Recommended Connection if No Diagnostics are Required
Vee

= 6 to

28V

20

10

SwRch
Select
Inputs

11

In 1
In 2

I

In 3

12

In 4

O•01 I'F

3
Enable
10 kl!.

0
0

13

+5V

Out 1

ooot

Error

CO

C

Error

Out 2

::0
47kl!.

--'

17

18

Thermal

4

Out 3

CS
19

Clock

Out 4

Data Output

TLlH/11026-27

Simple protection of the LMD18400 against supply voltage reversal. Loads will be energized through the Intrinsic
diodes In parallel with the power switches. The Schottky diode will add approximately O.2V to the logic input switching
thresholds and the logic output low levels.
Vee
20
r-_~L..._.....,O.lI'F
I
10

Switch
Select
Inputs

11
12

In 1

"I , U

+12V
OV--r--;-

t---------~

-12V

Vee

In2

IO.

In 3
In 4

01 I'F

3
Enabla

Enable
lOkI!.

13

Error

+5V

0
0

Outl~----~-----------------------,

ooot

CO

C

Error

::0

--'

17
Thermal

Thermal Shutdown

HC126

CS

Clock
Diagnostic
Data Output

4

2

IN4001

..---------.

Out 2 I-----~----~

18
Out 3 ~----~---------,

CS
Clock

19
Out4 I-----~....,

Circuit
Load

Lamp
Load

Data Output
Gnd Gnd Gnd Gnd

5
Schottky
Diode
recommended

16

IN5819

TLlH/11026-2B

6-36

Applications

(Continued)

Simple Light "Chaser"

Shift

Register

O.lpF

5Hztol0HZiUI~~g~~~~§~~~~@~RI
Cloak

+5V

o

0

•

•

TL/H/l1026-29

Parallelling switches for higher current capability. Positive temperature coefficient of the switch ON resistance
provides ballasting to evenly share the load current between the switches. Any combination of switches can be
paralleled. Required peak load current will depend upon the motor load. Motor speed control can be provided by a
PWM signal of up to 20 kHz applied to the motor drive Input lines.

20
In 1
'O
In 2
II
In 3

Molor
Drl.e
Inpuls

Ccp

14

IO.OI!'F

In 4
Enable

Enable

Error

+5V

...
0
0

Ei

Error

:::E
-'

Thermal
Shuldown

Oul I

IX)

Thermal

Oul2

Oul3

18

CS
Clock
Dlogncstlc
Dala Oulpul

Oul4

19

Dala Oulpul
2A DC
Molors

-

6-37

TL/H/l1026-30

Section 7
Surface Mount

Section 7 Contents
Surface Mount . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
AN-450 Small Outline (SO) Package Surface Mounting Methods-Parameters and Their
Effect on Product Reliability. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

7-2

7-3
7-23

U)

c

is::

~National

Semiconductor

o

c

::::s

Surface Mount
SURFACE MOUNT PACKAGING AT NATIONAL

DIPs) have a 100 mil lead center spacing. Surface mount
packages currently in production (e.g., SOT, SOIC, PCC,
LCC, LDCC) have a 50 mil lead center spacing. Surface
mount packages in production release (e.g., POFP) have a
25 mil lead center spacing. Surface mount packages in development (e.g., TAPEPAK®) will have a lead center spacing of only 12-20 mils.

To meet the growing demand for smaller packaging, National has developed a line of surface mount packages. Ranging in lead counts from 3 to 360, the package offerings are
summarized in Table I.
Lead center spacing keeps shrinking with each new generation of surface mount package. Traditional packages (e.g.,

TABLE I. Surface Mount Packages from National
Package
Type

Small Outline
Transistor
(SOT)

Small Outline
IC(SOIC)

Plastic Chip
Carrier (PCC)

Plastic Ouad
Flat Pack
(POFP)

Leadless Chip Leaded Chip
Carrier (LCG) Carrier
(LDCC)

,{]:: ~ ~ 0 [g 0
~

Package
Material

TAPEPAK®
(TP)

I

I

~

'11II1I1iI1I!1II1iI1I ,

!lnnnnnnn! I ~i]

Plastic

Plastic

Plastic

Plastic

Plastic

Ceramic

Ceramic

Gull Wing

Gull Wing

J-Bend

Gull Wing

Gull Wing

-

Gull Wing

Lead Center
Spacing

50 Mils

50 Mils

50 Mils

25 Mils

20,15,12 Mils

50 Mils

50 Mils

Tape & Reel
Option

Yes

Yes

Yes

tbd

tbd

No

No

Lead Bend

Lead Counts SOT-23
High Profile
SOT-23
Low Profile

80-8(*)
SO-14(*)

PCG-2Q(*)
PCC-28(*)

80-14 Wide(')
80-16(*)
80-16 Wide(')
SO-20(*)
80-24(')
80-28(0)

PCC-44(*)
PCG-68
PCC-84
PCC-124

POFP-84
POFP-100
POFP-132
POFP-196(')
POFP-244

TP-40(*)
TP-68
TP-84
TP-132
TP-172
TP-220
TP-284
TP-360

LCC-18
LCG-20(*)

LDCC-44

LCC-28

LDCC-68

LCC-32
LCG-44 (0)

LDCC-84

LCC-48
LCG-52
LCC-S8
LCC-84
LCC-124

LDCC-124

'In production (or planned) for linear products.

•
7-3

~ ,-------------------------------------------------------------------------------~

=

~

~

.
JJ

LINEAR PRODUCTS IN SURFACE MOUNT

TABLE II: Surface Mount Package
Thermal Resistance Range'

Linear functions available in surface mount include:
• Op amps

Package

• Comparators
• Regulators
• References

Thermal Resistance"
(6/A,'C/W)

SO-8
SO-14
SO-14 Wide
SO-lS
SO-lSWide
SO-20
SO-24
SO-28

• Data conversion
• Industrial
• Consumer
• Automotive
A representative list of linear part numbers in surface mount
is presented in Table III. Refer to the datasheet in the appropriate chapter of this databook for a complete description of the device. In addition, National has other products
and is continually expanding the list of devices offered in
surface mount. If the functions you need do not appear in
Table III, contact the sales office or distributor branch nearest you for additional information.

PCC-20
PCC-28
PCC-44

120-175
100-140
70-tl0
90-130
70-100
SO-90
55-85
TBD
70-100
SO-90
40-S0

• Actual thermal resistance for a particular device depends on die size.
Refer to the datasheet for the actual 8jA value.
"Test conditions: PCB mount (FR4 material). still air (room temperature).
copper traces (150 X 20 X 10 mils).

Automated manufacturers can improve their cost savings by
using Tape-and-Reel for surface mount devices. Simplified
handling results because hundreds-to-thousands of semiconductors are carried on a single Tape-and-Reel pack (see
ordering and shipping information-printed later in this section-for a comparison of devices/reel vs. devices/rail for
those surface mount package types being used for linear
products). With this higher device count per reel (when compared with less than a 100 devices per rail), pick-and-place
machines have to be re-Ioaded less frequently and lower
labor costs result.

Given a max junction temperature of 150'C and a maximum
allowed ambient temperature, the surface mount device will
be able to dissipate less power than the DIP device. This
factor must be taken into account for new designs.
For board conversion, the DIP and surface mount devices
would have to dissipate the same power. This means the
surface mount circuit would have a lower maximum allowable ambient temperature than the DIP circuit. For DIP circuits where the maximum ambient temperature required is
substantially lower than the maximum ambient temperature
allowed, there may be enough margin for safe operation of
the surface mount circuit with its lower maximum allowable
ambient temperature. But where the maximum ambient temperature required of the DIP current is close to the maximum allowable ambient temperature, the lower maximum
ambient temperature allowed for the surface mount circuit
may fall below the maximum ambient temperature required.
The circuit designer must be aware of this potential pitfall so
that an appropriate work-around can be found to keep the
surface mount package from being thermally overstressed
in the application.

With Tape-and-Reel, manufacturers save twice-once from
using surface mount technology for automated PC board
assembly and again from less device handling during shipment and machine set-up.
BOARD CONVERSION
Besides new designs, many manufacturers are converting
existing printed circuit board designs to surface mount. The
resulting PCB will be smaller, lighter and less expensive to
manufacture; but there is one caveat-be careful about the
thermal dissipation capability of the surface mount package.
Because the surface mount package is smaller than the traditional dual-in-line package, the surface mount package is
not capable of conducting as much heat away as the DIP
(i.e., the surface mount package has a higher thermal resistance-see Table II).

SURFACE MOUNT LITERATURE
National has published extensive literature on the subject of
surface mount packaging. Engineers from packaging, quality, reliability, and surface mount applications have pooled
their experience to provide you with practical hands-on
knowledge about the construction and use of surface mount
packages.

The silicon for most National devices can operate up to a
150'C junction temperature (check the datasheet for the
rare exception). Like the DIP, the surface mount package
can actually withstand an ambient temperature of up to
125'C (although a commercial temperature range device
will only be specified for a max ambient temperature of 70'C
and an industrial temperature range device will only be
specified for a max ambient temperature of 85'C). See
AN-33S, "Understanding Integrated Circuit Package Power
Capabilities", (reprinted in the appendix of each linear databook volume) for more information.

The applications note AN-450 "Surface Mounting Methods
and their Effect on Product Reliability" is referenced on
each SMD datasheet. In addition, "Wave Soldering of Surface Mount Components" is reprinted in this section for your
information.

7-4

.-------------------------------------------------------------------------~

Amplifiers and Comparators
Part Number

Part Number

LF451CM
LF453CM
LM10CWM
LM10CLWM
LM318M
LM3080M
LM4250M
LM611CM
LM6121M
LM613CWM
LM614CWM
LM6151WM
LM61811M
LM6218WM
LM6321M
LM6361M
LM6362M
LM6364M
LM6365M
LMC660CM
LMC662CM

LMC60221M
LMC60241M
LMC60321M
LMC60341M
LMC60411M
LMC60421M
LMC60441M
LMC60841M
LMC60641M
LMC60611M
LMC60811M
LMC60621M
LMC60821M
LMC64841M
LMC64821M
LPC660lM
LPC6611M
LPC6621M

Data Acquisition Products
Part Number
ADC08061 /2/4/8
ADC08161/4/8
ADC08031 /2/4/8
ADC08131/4/8
ADC08231/4/8
ADC0851/58
ADC10061/2/4
ADC10154/8
ADC1034/8
ADC10461/2/4
ADC1061
ADC10662/4
ADC12030/2/4/8

Part Number

Part Number
DS2004TM
DS3680M
DS75451M
DS75452M
DS75453M
DS75454M

Part Number

LM317LM
LM337LM
LM431ACM
LM723CM
LM2574M-3.3
LM2574M-5.0
LM2574M-12
LM2574M-15
LM2574M-ADJ
LM2574HVM-3.3
LM2574HVM-5.0
LM2574HVM-12
LM2574HVM-15
LM2574HVM-ADJ
LM2575M-5.0
LM2575M-12
LM2575M-15
LM2575M-ADJ
LM2575HVM-5.0
LM2575HVM-12
LM2575HVM-15
LM2575HVM-ADJ

LM2577M-12
LM2577M-15
LM2577M-ADJ
LM2578AM
LM2931AM-5.0
LM2931M-5.0
LM2931CM
LM2936M-5.0
LM3524DM
LM3578AM
LM78L05ACM
LM78L12ACM
LM78L15ACM
LM79L05ACM
LM79L12ACM
LM79L15ACM
LP2951ACM
LP2951CM
LP2952AIM
LP29521M
LP2953AIM
LP29531M

DAC0854
LM12454/8
LM34
LM35
LM4040
LM4041
LM4431
LMF100
LMF380
LMF40
LMF60
LMF90

~

o

c
;:,

Part Number

Part Number

AH5012CM
LF13331M
LF13509M
LF13333M
LM555CM
LM556CM
LM567CM
LM1496M
LM2917M
LM3046M
LM3086M
LM3146M

LM13600M
LM13700M
LMC555CM
LM567CM
MF4CWM-50
MF4CWM-100
MF6CWM-50
MF10CCWM
MF6CWM-100
MF5CWM
LMC568CM
LMC567CM

Commercial and Automotive

Regulators and References
Part Number

Part Number

~

CD

Industrial Functions

Peripheral Drivers
DS2001CM
DS200HM
DS2002CM
DS2002TM
DS2003CM
DS2003TM
DS2004CM

0
C

TABLE III. Linear Surface Mount Selected Device Listing

Part Number

Part Number

LM386M-1
LM831M
LM832M
LM833M
LM837M
LMC835V
LM1201M
LM1204V

LM1851M
LM1865M
LM1877M
LM1894M
LM1882CM
LM1964V
LMC1982CIV
LMC1983CIV
LM3361AM
LM1881M
LM3914V

,.
7-5

...C r-------------------------------------------------------------------------------------,
~

o

::::E

~
~

tn

A FINAL WORD
National is a world leader in the design and manufacture of
surface mount components.

Because of design innovations such as perforated copper
leadframes, our small outline package is as reliable as our
DIP-the laws of physics would have meant that a straight
"junior copy" of the DIP would have resulted in an "5.0."
package of lower reliability. You benefit from this equivalence of reliability. In addition, our ongoing vigilance at each
step of the production process assures that the reliability we
designed in stays in so that only devices of the highest quality and reliability are shipped to your factory.

Package

Package
Designator

Max/Rail

PerReel'

50-8
SO-14
SO-14 Wide
50-16
SO-16 Wide
50-20
SO-24
SO-28

M
M
WM
M
WM
M
M
M

100
50
50
50
50
40
30
26

2500
2500
1000
2500
1000
1000
1000
1000

V
V
V

50
40
25

1000
1000
500

PQFP-196

VF

TBD

TP-40

TP

100

E
E

50
25

PCL-20
PCL-28
PCL-44

Our surface mount applications lab at our headquarters site
in Santa Clara, California continues to research (and publish) methods to make it even easier for you to use surface
mount technology. Your problems are our problems.
When you think "Surface Mount"-think "National"l

LCC-20
LCC-44

Ordering and Shipping Information

-

TBD

'Incremental ordering quantities. (National Semiconductor reserves the right

When you order a surface mount semiconductor, it will be in
one of the several available surface mount package types.
Specifying the Tape-and-Reel method of shipment means
that you will receive your devices in the following quantities
per Tape-and-Reel pack: SMD devices can also be supplied
in conventional conductive rails.

to provide a smaller quantity of devices per Tape-and·Reel pack to preserve

lot or date code integrity. See example below.)

Example: You order 5,000 LM324MXICs shipped in Tapeand-Reel.
• Case 1: All 5,000 devices have the same date code
• You receive 2 50-14 (Narrow) Tape-and-Reel
packs, each having 2500 LM324M ICs

When ordering bulk S.O.-specify "M".
When ordering S.O. Tape & Reel-specify "MX".

• Case 2: 3,000 devices have date code A and 2,000 devices have date code B
• You receive 3 50-14 (Narrow) Tape-and-Reel
packs as follows:
Pack # 1 has 2,500 LM324MXICs with date code A
Pack # 2 has 500 LM324MXICs with date code A
Pack #3 has 2,000 LM324MXICs with date code B

Short-Form Procurement Specification
TAPE FORMAT

-+

Trailer (Hub End)'

Carrier'

IOIrectIoTtofFeed I
Leader (Start End)'

Empty Cavities,
min (Unsealed
Cover Tape)

Empty Cavities,
min (Sealed
Cover Tape)

Filled Cavities
(Sealed
Cover Tape)

Empty Cavities,
min (Sealed
Cover Tape)

Empty Cavities,
min (Unsealed
Cover Tape)

50-8 (Narrow)

2

2

2500

5

5

50-14 (Narrow)

2

2

2500

5

5

Small Outline IC

50-14 (Wide)

2

2

1000

5

5

SO-16 (Narrow)

2

2

2500

5

5

SO-16 (Wide)

2

2

1000

5

5

SO-20 (Wide)

2

2

1000

5

5

SO-24 (Wide)

2

2

1000

5

5

SO-28 (Wide)

0

25

1000

42

0

Plastic Chip carrier IC
PCC-20

2

2

1000

5

5

PCC-28

2

2

750

5

5

PCC-44

2

2

500

5

5

'The following diagram Identifies these secHons of the tape and Pin # 1 device orientation.

7-6

r--------------------------------------------------------------------------, cm
Short-Form Procurement Specification

~

(Continued)

DEVICE ORIENTATION

CD

3:

DIRECTION
OF FEED

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~ TRAILER ---.~r._--------CARRIERSECTION _ _ _ _ _ _ _ _ _
I~-SECTION

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• EMPTY
CAVITIES
• UNSEALED
COVER TAPE

~--~~~~~;1
.'.EM~Y
CAVITIES

• EMPTY
CAVITIES
• SEALED
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SO-IC
DEVICES

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• EMPTY
CAVITIES
• UNSEALED
COVER TAPE

PCC-IC
DEVICES
TL/XX/0026-6

• Reel:

MATERIALS
• Cavity Tape: Conductive PVC (less than 105 Ohms/Sq)

(1) Solid 80 pt fibreboard (standard)

• Cover Tape: Polyester

(2) Conductive fibreboard available
(3) Conductive plastic (PVC) available

(1) Conductive cover available
TAPE DIMENSIONS (24 MIllimeter Tape or Less)
_

Po 10 PITCH CUMULATIVE
TAPE TOLERANCE ±O.2mm

Dl

,

DEVICE ORIENTATION

PIN
1

fI

SO·IC
PCC·IC
TUXX/0026-9

7-7

Short-Form Procurement Specification

I

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P2

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(Continued)

D

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Ao

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IR

Small Outline IC
50-8
12±.30 B.0±.10
(Narrow)

5.5±.05 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 6.4±.10

5.2±.10

2.1 ±.10 1.55±.05 30

50-14
16±.30 B.0±.10
(Narrow)

7.5±.10 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 6.5±.10

9.0±.10

2.1 ±.10 1.55±.05 40

9.5±.10

3.0±.10 1.55±.05 40

50-14
(Wide)

16±.30 12.0±.10 7.5±.10 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 10.9±.10

50-16
16±.30 B.0±.10
(Narrow)

7.5±.10 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 6.5±.10

10.3±.10 2.1 ±.10 1.55±.05 40

50-16
(Wide)

16±.30 12.0±.10 7.5±.10 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 10.9±.10 10.76±.10 3.0±.10 1.55±.05 40

50-20
(Wide)

24±.30 12.0±.10 11.5±.10 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 10.9±.10 13.3±.10 3.0±.10 2.05±.05 50

50-24
(Wide)

24±.30 12.0±.10 11.5±.10 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 10.9±.10 15.85±.10 3.0±.10 2.05±.05 50

Plastic Chip Carrier IC
PCC-20

16±.30 12.0±.10 7.5±.10 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 9.3±.10

PCC-28

24±.30 16.0±.10 11.5±.10 1.75±.10 2.0±.05 4.0±.10 1.55±.05 .30±.10 13.0±.10 13.0± .10 4.9±.10 2.05±.05 50

9.3±.10

4.9±.10 1.55±.05 40

Note 1: Ao. Bo and Ko dimensions are measured 0.3 mm above the inside wall of the cavity bottom.
Note

2: Tape with

components shall pass around a mandril radius R without damage.

Note 3: Cavity tape material shall be PVC conductive (less than 105 Ohms/Sq).
Note 4: Cover tape material shall be polyester (30-65 grams peel-back force).
Note 5: 01 Dimension is centered within cavity.
Note 6: All dimensions 'are in millimeters.

REEL DIMENSIONS
TMAX

-

H

1-8
LABELeD

A

/

Dd:i

"-

( (OJ )

'-_/'

C::r:=

~ ~ru"_,
M
STARTM' Surface Mount Tape and Reel

7-8

TL/XX/OO26-10

r---------------------------------------------------------------------------------, c
Short-Form Procurement Specifications (Continued)
iiig
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A (Max)

B(Min)

C

D(Mln)

N (Min)

G

T(Max)

(13.00)
(330)

.059
-1.5

.512±.002
13±0.05

.795
-20.2

1.969
50

--

0.488~:g~g

.724

12.4~8

18.4

SO-14 (Narrow)
SO-14 (Wide)
SO-16 (Narrow)
SO-16 (Wide)
PCC-20

(13.00)
(330)

-1.5

.059

.512±.002
13±0.05

.795
-20.2

--

1.969
50

0.646~:g~g

.882
-22.4

SO-20 (Wide)
SO-24 (Wide)
PCC-28

(13.00)
(330)

.059

.512±.002
13±0.05

.795
-20.2

1.969

0.960~:g~g

50

24.4~8

(13.00)
(330)

.059

.512±.002
13±0.05

.795
-20.2

1.969
50

12mmTape

SO-8 (Narrow)

16 mmTape

24 mm Tape

32mmTape

PCC-44

1.5

1.5

2
164+
. -0

1.276~:g~g
32.4~8

1.197
30.4
1~12

38.4

Inches
Units: Millimeters
Material: Paperboard (Non-Flaking)
LABEL
Human and Machine Readable Label is provided on reel. A
variable (C.P.I) density code 39 is available. NSC STD label
(7.6 C.P.I.)

Wave Soldering of Surface
Mount Components
ABSTRACT
In facing the upcoming surge of "surface mount technology", many manufacturers of printed circuit boards have taken steps to convert some portions of their boards to this
new process. However, as the availability of surface mount
components is still limited, may have taken to mixing the
lead-inserted standard dual-in-line packages (DIPs) with the
surface mounted devices (SMDs). Furthermore, to take advantage of using both sides of the board, surface-mounted
components are generally adhered to the bottom side of the
board while the top side is reserved for the conventional
lead-inserted packages. If processed through a wave solder
machine, the semiconductor components are now subjected to extra thermal stresses (now that the components are
totally immersed into the molten solder).
A discussion of the effect of wave soldering on the reliability
of plastic semiconductor packages follows. This is intended
to highlight the limitations which should be understood in
the use of wave soldering of surface mounted components.

FIELD
Lot Number
Date Code
Revision Level
National Part No. I.D.
Qty.
EXAMPLE
LOT

REVISION
( NUMBER

(NUMBER

LOT:

EPb3~3b3K027

R:

TL/XX/0026-11

Fields are separated by at least one blank space.
Future Tape-and-Reel packs will also include a smaller-size
bar code label (high-density code 39) at the beginning of the
tape. (This tape label is not available on current production.)
National Semiconductor will also offer additional labels containing information per your specific specification.

ROLE OF WAVE-SOLDERING IN
APPLICATION OF SMDs
The generally acceptable methods of soldering SMDs are
vapor phase reflow soldering and IR reflow soldering, both
requiring application of solder paste on PW boards prior to
placement of the components. However, sentiment still exists for retaining the use of the old wave-soldering machine.

7-9

5:

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C

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Wave Soldering of Surface Mount Components (Continued)
The reasons being:

C) Vapor/lR reflow only.

1) Most PC Board Assembly houses already possess wave
soldering equipment. Switching to another technology
such as vapor phase soldering requires substantial investment in equipment and people.
2) Due to the limited number of devices that are surface
mount components, it is necessary to mix both lead inserted components and surface mount components on
the same board.
3) Some components such as relays and switches are
made of materials which would not be able to survive the
temperature exposure in a vapor phase or IR furnace.

1. Components on the same side of PW Board.
Trim and form standard DIPs in "gull wing" configuration
Solder paste screened on PW Board
Pick and place SMDs and DIPs
Bake
Vapor/IR reflow
Clean
2. Components on opposite sides of PW Board.
Solder paste screened on SMD-side of Printed
Wire Board

PW BOARD ASSEMBLY PROCEDURES
There are two considerations in which through-hole ICs may
be combined with surface mount components on the PW
Board:
a) Whether to mount ICs on one or both sides of the board.
b) The sequence of soldering using Vapor Phase, IR or
Wave Soldering singly or combination of two or more
methods.

Adhesive dispensed at central location of each
component
Pick and place SMDs
Bake
Solder paste screened on all pads on DIP-side or
alternatively apply solder rings (performs) on
leads

The various processes that may be employed are:

Lead insert DIPs
Vapor/IR reflow

A) Wave Solder before VaporliR reflow solder.
1. Components on the same side of PW Board.
Lead insert standard DIPS onto PW Board Wave
solder (conventional)

Clean and lead trim
D) Wave Soldering Only
1. Components on opposite sides of PW Board.
Adhesive dispense on SMD side of PW Board

Wash and lead trim
Dispense solder paste on SMD pads

Pick and place SMDs

Pick and place SMDs onto PW Board
Bake
Vapor phase/lR reflow

Cure adhesive
Lead insert top side with DIPs
Wave solder with SMDs down and into solder bath
Clean and lead trim

Clean
2. Components on opposite side of PW Board.

All of the above assembly procedures can be divided into
three categories for I.C. Reliability considerations:

Lead insert standard DIPs onto PW Board
Wave Solder (conventional)
Clean and lead trim

1) Components are subjected to both a vapor phase/lR
heat cycle then followed by a wave-solder heat cycle or
vice versa.
2) Components are subjected to only a vapor phaseliR
heat cycle.

Invert PW Board
Dispense solder paste on SMD pads
Dispense drop of adhesive on SMD sites (optional
for smaller components)

3) Components are subjected to wave-soldering only and
SMDs are subjected to heat by immersion into a solder
pot.

Pick and place SMDs onto board
Bake/Cure

Of these three categories, the last is the most severe regarding heat treatment to a semiconductor device. However, note that semiconductor molded packages generally
possess a coating of solder on their leads as a final finish
for solderability and protection of base leadframe material.
Most semiconductor manufacturers solder-plate the component leads, while others perform hot solder dip. In the latter
case the packages may be subjected to total immersion into
a hot solder bath under controlled conditions (manual operation) or be partially immersed while in a 'pallet' where automatic wave or DIP soldering processes are used. It is, therefore, possible to subject SMDs to solder heat under certain
conditions and not cause catastrophic failures.

Invert board to rest on raised fixture
Vapor/lR reflow soldering
Clean
B) Vapor/lR reflow solder then Wave Solder.
1. Components on the same side of PW Board.
Solder paste screened on SMD side of Printed
Wire Board
Pick and place SMDs
Bake
VaporliR reflow
Lead insert on same side as SMDs
Wave solder
Clean and trim underside of PCB

7-10

en
c

Wave Soldering of Surface Mount Components (Continued)
THERMAL CHARACTERISTICS OF
MOLDED INTEGRATED CIRCUITS

EFFECT ON PACKAGE PERFORMANCE BY
EPOXY-METAL SEPARATION
In wave soldering, it is necessary to use fluxes to assist the
solderability of the components and PW boards. Some facilities may even process the boards and components through
some form of acid cleaning prior to the soldering temperature. If separation occurs, the flux residues and acid residues (which may be present owing to inadequate cleaning)
will be forced into the package mainly by capillary action as
the residues move away from the solder heat source. Once
the package is cooled, these contaminants are now trapped
within the package and are available to diffuse with moisture
from the epoxy over time. It should be noted that electrical
tests performed immediately after soldering generally will
give no indication of this potential problem. In any case, the
end result will be corrosion of the chip metallization over
time and premature failure of the device in the field.

Since Plastic DIPs and SMDs are encapsulated with a thermoset epoxy, the thermal characteristics of the material
generally correspond to a TMA (Thermo-Mechanical Analysis) graph. The critical parameters are (a) its Linear thermal
expansion characteristics and (b) its glass transition temperature after the epoxy has been fully cured. A typical TMA
graph is illustrated in Figure 1. Note that the epoxy changes
to a higher thermal expansion once it is subjected to temperatures exceeding its glass transition temperature. Metals
(as used on lead frames, for example) do not have this characteristic and generally will have a consistent Linear thermal
expansion over the same temperature range.
In any good reliable plastic package, the choice of lead
frame material should be such to match its thermal expansion properties to that of the encapsulating epoxy. In the
event that there is a mismatch between the two, stresses
can build up at the interface of the epoxy and metal. There
now exists a tendency for the epoxy to separate from the
metal lead frame in a manner similar to that observed on bimetallic thermal range.

iiig
iii:

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VAPOR PHASE/IR REFLOW SOLDERING
In both vapor phase and IR reflow soldering, the risk of
separation between epoxy/metal can also be high. Operating temperatures are 215'C (vapor phase) or 240'C (IR) and
duration may also be longer (30 sec-60 sec). On the same
theoretical basis, there should also be separation. However,
in both these methods, solder paste is applied to the pads
of the boards; no fluxes are used. Also, the devices are not
immersed into the hot solder. This reduces the possibility of
solder forcing itself into the epoxy-lead frame interface. Furthermore, in the vapor phase system, the soldering environment is "oxygen-free" and considered "contaminant free".
Being so, it could be visualized that as far as reliability with
respect to corrosion, both of these methods are advantageous over wave soldering.

In most cases when the packages are kept at temperatures
below their glass transition, there is a small possibility of
separation at the expoxy-metal interface. Howerver, if the
package is subjected to temprature above its glass-transition temperature, the epoxy will begin to expand much
faster than the metal and the probability of separation is
greatly increased.
CONVENTIONAL WAVE-SOLDERING
Most wave-soldering operations occur at temperatures between 240-260·C. Conventional epoxies for encapsulation
have glass-transition temperature between 140-170·C. An
I.C. directly exposed to these temperatures risks its long
term functionality due to epoxy/metal separation.

BIAS MOISTURE TEST
A bias moisture test was deSigned to determine the effect
on package performance. In this test, the packages are
pressured in a stream chamber to accelerate penetration of
moisture into the package. An electrical bias is applied on
the device. Should there be any contaminants trapped within the package, the moisture will quickly form an electrolyte
and cause the electrodes (which are the lead fingers), the
gold wire and the aluminum bond-pads of the silicon device
to corrode. The aluminum bond-pads, being the weakest
link of the system, will generally be the first to fail.

Fortunately, there are factors that can reduce that element
of risk:
1) The PW board has a certain amount of heat-sink effect
and tends to shield the components from the temperature of the solder (if they were placed on the top side of
the board). In actual measurements, DIPs achieve a temperature between 120-150'C in a 5-second pass over
the solder. This accounts for the fact that DIPs mounted
in the conventional manner are reliable.
2) In conventional soldering, only the tip of each lead in a
DIP would experience the solder temperature because
the epoxy and die are standing above the PW board and
out of the solder bath.

This proprietary accelerated bias/moisture pressure-test is
significant in relation to the life test condition at 85'C and

z

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100 110 120 130 140 150 160 t170 180
Tg
FIGURE 1. Thermal Expansion and Glass Transition Temperature
7-11

TLlXX/0026-12

Wave Soldering of Surface Mount Components (Continued)
85% relative humidity. Once cycle of approximately 100
hours has been shown to be equivalent to 2000 hours in the
85/85 condition. Should the packages start to fail within the
first cycle in the test, it is anticipated that the boards with
these components in the harsh operating environment
(85'C/85% RH) will experience corrosion and eventual
electrical failures within its first 2000 hours of operation.

Since the package is of very small mass and experiences a
rather sharp thermal shock followed by stresses created by
the mismatch in expansion, the results show the package
being susceptible to failures aiter being immersed in excess
of 6 seconds in a solder pot. In the second case where the
packages were mounted, the effect of severe temperature
excursion was reduced. In the second case where the packages were mounted, the effect of severe temperature excursion was reduced. In any case, because of the repeated
treatment, the package had failures when subjected in excess of 6 seconds immersion in hot solder. The safety margin is therefore recommended as maximum 4 seconds immersion. If packages were immersed longer than 4 seconds, there is a probable chance of finding some long term
reliability failures even though the immediate electrical test
data could be acceptable.
Finally, Table VI examines the bias moisture test performed
on surface mount (SOIC) components manufactured by various semiconductor houses. End point was an electrical test
aiter an equivalent of 6000 hours in a 85/85 test. Failures
were analyzed and corrosion was checked for in each case
to detect flaws in package integrity.

Whether this is significant to a circuit board manufacturer
will obviously be dependent on the products being manufactured and the workmanship or reliability standards. Generally in systems with a long warranty and containing many
components, it is advisable both on a reputation and cost
basis to have the most reliable parts available.
TEST RESULTS
The comparison of vapor phase and wave-soldering upon
the reliability of molded Small-Outline packages was performed using the bias moisture test (see Table IV). It is
clearly seen that vapor phase reflow soldering gave more
consistent results. Wave-soldering results were based on
manual operation giving variations in soldering parameters
such as temperature and duration.
TABLE IV. Vapor Phase vs. Wave Solder

TABLE VI. U.S. Manufacturers Integrated Circuits
Reliability In Various Solder Environments
(# Failure/Total Tested)

1. Vapor phase (60 sec. exposure @215'C)
= 9 failures/1723 samples
= 0.5% (average over 32 sample lots)
2. Wave solder (2 sec total immersion @260'C)
= 16 failures/1201 samples
= 1.3% (average over 27 sample lots)
Package: SO-14 lead
Test:
Bias moisture test 85% R.H.,
85'C for 2000 hours
Device:
LM324M
In Table V we examine the tolerance of the Small-Outlined
(SOIC) package to varying immersion time in a hot solder
pot. SO-14 lead molded packages were subjected to the
bias moisture test after being treated to the various soldering conditions and repeated four (4) times. End point was an
electrical test aiter an equivalent of 4000 hours 85/85 test.
Results were compared for packages by itself against packages which were surface-mounted onto a FR-4 printed wire
board.

Unmounted

Mounted

0/114

0/84

Solder Dip
2 sec @260'C

2/144(1.4%)

0/85

Solder Dip
4sec@260'C

-

0/83

Solder Dip
6 sec @260'C

13/248 (5.2%)

1/76(1.3%)

14/127 (11.0%)

3/79 (3.8%)

Solder Dip
10 sec @260'C
Package:
Device:

Vapor
Phase
30 sec

Wave
Solder
2 see

Wave
Solder
4 see

Wave
Solder
6 see

Wave
Solder
10 see

ManufA
ManufB
ManufC

8/30·
2/30·
0/30

1/30'

0.30
2/30'

12/30·

8/30'

22/30'

16/30·
20/30'

ManufD
ManufE
ManufF
ManufG

1/30·
1/30"
0/30
0/30

0/29

0/29

0/30

0/30

0/30
0/30

12/30·
0/30
0/30
0/30

14/30·

2130·

0/30

0/30
0/30

0/30
0/30

0/30
0/30

0/30

·Corrosion-failures

··No Visual Defects-Nan-corrosion failures
Test Accelerated Bias Moisture Test: 8S% R.H.l8S'C, 6000 equivalent

hours.

SUMMARY
Based on the results presented, it is noted that surfacemounted components are as reliable as standard molded
DIP packages. Whereas DIPs were never processed by being totally immersed in a hot solder wave during printed circuit board soldering, surface mounted components such as
SOICs (Small Outline) are expected to survive a total immersion in the hot solder in order to capitalize on maximum
population on boards. Being constructed from a thermoset
plastic of relatively low Tg compared to the soldering temperature, the ability of the package to survive is dependent
on the time of immersion and also the cleanliness of material. The results indicate that one should limit the immersion
time of package in the solder wave to a maximum of 4 seconds in order to truly duplicate the reliability of a DIP. As the
package size is reduced, as in a SO-8 lead, the requirement
becomes even more critical. This is shown by the various
manufacturers' performance. Results indicate there is room
for improvement since not all survived the hot solder immersion without compromise to lower reliability.

TABLE V. Summary of Wave Solder Results
(85% R.H./85'C Bias Moisture Test, 2000 hours)
(# Failures/Total Tested)

Control/Vapor Phase
15 sec@ 215'C

Package
SO-8

SO-14 lead
LM324M
7-12

(/)

Small Outline (SO) Package Surface Mounting MethodsParameters and Their Effect on Product Reliability
The SO (small outline) package has been developed to
meet customer demand for ever-increasing miniaturization
and component density.

In order to achieve reliability performance comparable to
DIPs-SO packages are designed and built with materials
and processes that effectively compensate for their small
size.
All SO packages tested on 85%RA, 85'C were assembled
on PC conversion boards using vapor-phase reflow soldering. With this approach we are able to measure the effect of
surface mounting methods on reliability of the process. As
illustrated in Figure A no significant difference was detected
between the long term reliability performance of surface
mounted S.O. packages and the DIP control product for up
to 6000 hours of accelerated 85%/85'C testing.

COMPONENT SIZE COMPARISON
S.O. Package

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SURFACE-MOUNT PROCESS FLOW
The standard process flowcharts for basic surface-mount
operation and mixed-lead insertion/surface-mount operations, are illustrated on the following pages.

TYPICALLY 0.050" LEADSPACING
TL/XX/0026-13

Standard DIP Package

Usual variations encountered by users of SO packages are:
• Single-sided boards, surface-mounted components only.
• Single-sided boards, mixed-lead inserted and surfacemounted components.
• Double-sided boards, surface-mounted components only.
• Double-sided boards, mixed-lead inserted and surfacemounted components.

1_

In consideration of these variations, it became necessary for
users to utilize techniques involving wave soldering and adhesive applications, along with the commonly-used vaporphase solder reflow soldering technique.
PRODUCTION FLOW

TYPICALLY 0.100" LEADSPACING
TL/XX/0026-14

Basic Surface-Mount Production Flow

Because of its small size, reliability of the product assembled in SO packages needs to be carefully evaluated.
SO packages at National were internally qualified for production under the condition that they be of comparable reliability performance to a standard dual in line package under
all accelerated environmental tests. Figure A is a summary
of accelarated bias moisture test performance on 30V bipolar and 15V CMOS product assembled in SO and DIP (control) packages.
V+

=15VCMOS

30V BIPOLAR
85% RH/85"C
TEST CONDITION
DIP

o

2000

4000

6000

TEST TIME (HRS)
TL/XX/0026-15

fI

FIGURE A

7-13

Mixed Surface-Mount and Axial-Leaded Insertion
Components Production Flow

Thermal stress of the packages during surface-mounting
processing is more severe than during standard DIP PC
board mounting processes. Figure 8 illustrates package
temperature versus wave soldering dwell time for surface
mounted packages (components are immersed Into the
molten solder) and the standard DIP wave soldering process. (Only leads of the package are immersed into the molten solder).
SOLDER TEMPERATURE 2600(;

o

1 2 3 4 5 6 7 8 9 10 SEC.
DWELL TIME
TUXX/0026-18

FIGUREB
For an ideal package, the thermal expansion rate of the
encapsulant should match that of the leadframe material in
order for the package to maintain mechanical integrity during the soldering process. Unfortunately, a perfect matchup
of thermal expansion rates with most presently used packaging materials is scarce. The problem lies primarily with the
epoxy compound.
Normally, thermal expansion rates for epoxy encapsulant
and metal lead frame materials are linear and remain fairly
close at temperatures approaching t60·C, Figure C. At lower temperatures the difference in expansion rate of the two
materials is not great enough to cause interface separation.
However, when the package reaches the glass-transition
temperature (Tg) of epoxy (typically t60-16S·C), the thermal expansion rate of the encapsulant increases sharply,
and t~e material undergoes a transition into a plastic state.
The epoxy begins to expand at a rate three times or more
greater than the metal leadframe, causing a separation at
the interface.

TL/XX/0026-17

al

100 110 120 130 140 150 160 :170 180

Tg

T(OC)
TL/XX/0026-19

FIGUREC

7-14

r---------------------------------------------------------------------------------,
When this happens during a conventional wave soldering
process using flux and acid cleaners, process residues and
even solder can enter the cavity created by the separation
and become entrapped when the material cools. These
contaminants can eventually diffuse into the interior of the
package, especially in the presence of moisture. The result
is die contamination, excessive leakage, and even catastrophic failure. Unfortunately, electrical tests performed immediately following soldering may not detect potential flaws.

The basic component-placement systems available are
classified as:
(a) In-line placement
-

Fixed placement stations
Boards indexed under head and respective components placed
(b) Sequential placement
-

Most soldering processes involve temperatures ranging up
to 260'C, which far exceeds the glass-transition temperature of epoxy. Clearly, circuit boards containing SMD packages require tighter process controls than those used for
boards populated solely by DIPs.

Either a X-V moving table system or a 0, X-V moving
pickup system used

-Individual components picked and placed onto boards
(c) Simultaneous placement
-

Figure D is a summary of accelerated bias moisture test
performance on the 30V bipolar process.
Group 1 - Standard DIP package
Group 2 - SO packages vapor-phase reflow soldered on
PC boards
Group 3-6 SO packages wave soldered on PC boards
Group 3 - dwell time 2 seconds
4 - dwell time 4 seconds
5 - dwell time 6 seconds
6 - dwell time 10 seconds

Multiple pickup heads
Whole array of components placed onto the PCB at
the same time

(d) Sequential/simultaneous placement
- X-V moving table, multiple pickup heads system
- Components placed on PCB by successive or simUltaneous actuation of pickup heads
The SO package is treated almost the same as surfacemount, passive components requiring correct orientation in
placement on the board.
Pick and Place Action

#6(10 SEC)

#5(6 SEC)
#4(4 SEC)

o

2000

4000

6000

TEST TIME (HRS)
TL/XX/0026-20

FIGURED
It is clear based on the data presented that SO packages
soldered onto PC boards with the vapor phase reflow process have the best long term bias moisture performance
and this is comparable to the performance of standard DIP
packages. The key advantage of reflow soldering methods
is the clean environment that minimized the potential for
contamination of surface mounted packages, and is preferred for the surface-mount process.

TLlXX/0026-21

BAKE
This is recommended, despite claims made by some solder
paste suppliers that this step be omitted.
The functions of this step are:

When wave soldering is used to surface mount components
on the board, the dwell time of the component under molten
solder should be no more than 4 seconds, preferrably under
2 seconds in order to prevent damage to the component.
Non-Halide, or (organic acid) fluxes are highly recommended.

• Holds down the solder globules during subsequent reflow
soldering process and prevents expulsion of small solder
balls.
o Acts as an adhesive to hold the components in place during handling between placement to rellow soldering.

PICK AND PLACE

• Holds components in position when a double-sided surface-mounted board is held upside down going into a vapor-phase reflow soldering operation.

The choice of automatic (all generally programmable) pickand-place machines to handle surface mounting has grown
considerably, and their selection is based on individual
needs and degree of sophistication.

• Removes solvents which might otherwise contaminate
other equipment.
• Initiates activator cleaning of surfaces to be soldered.
• Prevents moisture absorption.

7-15

en
c

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o

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:::::II

o

::::E
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:::::II

(/)

The process is moreover very simple. The usual schedule is
about 20 minutes in a 65·C-95·C (dependent on solvent
system of solder paste) oven with adequate venting. Longer
bake time is not recommended due to the following reasons:

In·Llne Conveyorized Vapor·Phase Soldering
CONDENSATION

J

• The flux will degrade and affect the characteristics of the
paste.

--- I

• Solder globules will begin to oxidize and cause sOlderability problems.
• The paste will creep and after reflow, may leave behind
residues between traces which are difficult to remove and
vulnerable to electro-migration problems.

-

_"a

..J:.

-BaT --";:;!':. -

-

-

- - -

COILS

1-----

COILS

c:::=:::> c:::=:::> c:::=:::>
LIQUID

REFLOW SOLDERING
There are various methods for reflowing the solder paste,
namely:
•
•
•
•

~
- L
IMMERSION HEATER

TL/XX/0026-22

The question of thermal shock is asked frequently because
of the relatively sharp increase in component temperature
from room temperature to 215·C. SO packages mounted on
representative boards have been tested and have shown
little effect on the integrity of the packages. Various packages, such as cerdips, metal cans and TO-5 cans with glass
seals, have also been tested.

Hot air reflow
Infrared heating (furnaces)
Convectional oven heating
Vapor-phase reflow soldering

• Laser soldering
For SO applications, hot air reflow/infrared furnace may be
used for low-volume production or prototype work, but vapor-phase soldering reflow is more efficient for consistency
and speed. Oven heating is not recommended because of
"hot spots" in the oven and uneven melting may result. laser soldering is more for specialized applications and requires a great amount of investment.

Vapor·Phase Furnace

HOT GAS REFLOW/INFRARED HEATING
A hand-held or table-mount air blower (with appropriate orifice mask) can be used.
The boards are preheated to about 100·C and then subjected to an air jet at about 260·C. This is a slow process and
results may be inconsistent due to various heat-sink properties of passive components.
Use of an infrared furnace is the next step to automating the
concept, except that the heating is promoted by use of IR
lamps or panels. The main objection to this method is that
certain materials may heat up at different rates under IR
radiation and may result in damage to these components
(usually sockets and connectors). This could be minimized
by using far-infrared (non-focused) system.
TLlXX/0026-23

VAPOR·PHASE REFLOW SOLDERING
Currently the most popular and consistent method, vaporphase soldering utilizes a fluoroinert fluid with excellent
heat-transfer properties to heat up components until the solder paste reflows. The maximum temperature is limited by
the vapor temperature of the fluid.

Batch·Fed Production Vapor·Phase Soldering Unit
SECONDARY
COILS

The commonly used fluids (supplied by 3M Corp) are:
PRIMARY COILS

• FC-70, 215·C vapor (most applications) or FX-38
• FC-71 , 253·C vapor (low-lead or tin-plate)
HTC, Concord, CA, manufactures equipment that utilizes
this technique, with two options:
• Batch systems, where boards are lowered in a basket and
subjected to the vapor from a tank of boiling fluid.
• In-line conveyorized systems, where boards are placed
onto a continuous belt which transports them into a concealed tank where they are subjected to an environment
of hot vapor.
Dwell time in the vapor is generally on the order of 15-30
seconds (depending on the mass of the boards and the
loading density of boards on the belt).
7-16

.--------------------------------------------------------------------------.0
Solder Joints on a SO-14 Package on PCB

Solder Joints on a 50-14 Package on PCB

C

;.
g

3:

oC

:::::I

TLlXXI0026-25

TLIXXI0026-26

PRINTED CIRCUIT BOARD

The typical lithographic "footprints" for SO packages are
illustrated below. Note that the 0.050" lead center-center
spacing is not easily managed by commercially-available air
pressure, hand-held dispensers.
Using a stainless-steel, wire-mesh screen stencilled with an
emulsion image of the substrate pads is by far the most
common and well-tried method. The paste is forced through
the screen by a V-shaped plastic squeegee in a sweeping
manner onto the board placed beneath the screen.
The setup for SO packages has no special requirement
from that required by other surface-mounted, passive components. Recommended working specifications are:
o Use stainless-steel, wire-mesh screens, #80 or #120,
wire diameter 2.6 mils. Rule of thumb: mesh opening
should be approximately 2.5-5 times larger than the average particle size of paste material.
o Use squeegee of Durometer 70.

The SO package is molded out of clean, thermoset plastic
compound and has no particular compatibility problems with
most printed circuit board substrates.
The package can be reliably mounted onto substrates such
as:
• G10 or FR4 glass/reSin
• FR5 glass/resin systems for high-temperature
applications
• Polymide boards, also high-temperature
applications
• Ceramic substrates
General requirements for printed circuit boards are:
• Mounting pads should be solder-plated whenever
applicable.
• Solder masks are commonly used to prevent solder bridging of fine lines during soldering.

o Experimentation with squeegee travel speed is recom-

mended, if available on machine used.

The mask also protects circuits from processing chemical
contamination and corrosion.

• Use solder paste of mesh 200-325.
o Emulsion thickness of 0.005" usually used to achieve a
solder paste thickness (wet) of about 0.008" typical.

If coated over pre-tinned traces, residues may accumulate
at the mask/trace interface during subsequent reflow,
leading to possible reliability failures.

• Mesh pattern should be 90 degrees, square grid.

Recommended application of solder resist on bare, clean
traces prior to coating exposed areas with solder.

• Snap-off height of screen should not exceed
damage to screens and minimize distortion.

General requirements for solder mask:
- Good pattern resolution.
- Complete coverage of circuit lines and resistance to
flaking during soldering.

Yo" , to avoid

SOLDER PASTE
Selection of solder paste tends to be confusing, due to numerous formulations available from various manufacturers.
In general, the following guidelines are sufficient to qualify a
particular paste for production:
• Particle sizes (see photographs below). Mesh 325 (approximately 45 microns) should be used for general purposes, while larger (solder globules) particles are preferred for leadless components (LCC). The larger particles
can easily be used for SO packages.

- Adhesion should be excellent on substrate material to
keep off moisture and chemicals.
- Compatible with soldering and cleaning requirements.
SOLDER PASTE SCREEN PRINTING
With the initial choice of printed circuit lithographic design
and substrate material, the first step in surface mounting is
the application of solder paste.

7-17

fI

• Composition, generally 60/40 or 63/37 Sn/Pb. Use 62/36
Sn/Pb with 2% Ag in the presence of Au on the soldering
area. This formulation reduces problems of metal leaching
from soldering pads.

• Uniform particle distribution. Solder globules should be
spherical in shape with uniform diameters and minimum
amount of elongation (visual under 100/200 x magnification). Uneven distribution causes uneven melting and subsequent expulsion of smaller solder balls away from their
proper sites.

• RMA flux system usually used.
• Use paste with aproximately 88-90% solids.

RECOMMENDED SOLDER PADS FOR SO PACKAGES

so·a, SO·14, SO·16

SO·16L, S0-20

1111_

0.045" :!:0.005"

r····~

. . ., '

L••••
~·
--l I-

0.245"

0.030" :!: 0.005"

0.160"

--I I-

1

0.050" TYP
TL/XX/0026-27

0.030"

'.J. '
L••••
~
1- --l
!;..

:!:0.005"~

I_~TYP

TUXX/OO26-28

TL/XX/0026-29

Comparison of Particle Size/Shape of Various Solder Pastes
200

x Alpha (62/36/2)

200

x Kester (63/37)

TUXX/0026-31

TL/XX/0026-30

7·18

en
c

Comparison of Particle Size/Shape of Various Solder Pastes (Continued)
Solder Paste Screen on Pads

iiig

200 x Fry Metal (63/37)

s::

o

c

~

TL/XX/0026-33

TL/XX/0026-32

200 ESL (63/37)

TLlXXlOO26-34

•
7-19

~

C
::::I

o

r------------------------------------------------------------------------------------------,
CLEANING

Hot-Air Rework Machine

~

The most critical process in surface mounting SO packages
is in the cleaning cycle. The package is mounted very close
to the surface of the substrate and has a tendency to collect
residue left behind after reflow soldering.

rn

Important considerations in cleaning are:

::E
cu

::::I

• Time between soldering and cleaning to be as short as
possible. Residue should not be allowed to solidify on the
substrate for long periods of time, making it difficult to
dislodge.
• A low surface tension solvent (high penetration) should be
employed. Solvents commercially available are:
Freon TMS (general purpose)
Freon TE35/TP35 (cold-dip cleaning)
Freon TES (general purpose)

TLlXX/0026-36

lead tips or, if necessary, solder paste can be dispensed
onto the pads using a varimeter. After being placed into
pOSition, the solder is reflowed by a hot-air jet or even a
standard soldering iron.

It should also be noted that these solvents generally will
leave the substrate surface hydrophobic (moisture repellent), which is desirable.

WAVE SOLDERING

Prelete or 1,1,1-Trichloroethane
Kester 5120/5121

In a case where lead insertions are made on the same
board as surface-mounted components, there is a need to
include a wave-soldering operation in the process flow.
Two options are used:

• A defluxer system which allows the workpiece to be subjected to a solvent vapor, followed by a rinse in pure solvent and a high-pressure spray lance are the basic requirments for low-volume production.

• Surface mounted components are placed and vapor
phase reflowed before auto-insertion of remaining components. The board is carried over a standard wave-solder
system and the underside of the board (only lead-inserted
leads) soldered.

• For volume production, a conveyorized, multiple hot solvent spray/jet system is recommended.
• Rosin, being a natural occurring material, is not readily
soluble in solvents, and has long been a stumbling block
to the cleaning process. In recent developments, synthetic flux (SA flux), which is readily soluble in Freon TMS
solvent, has been developed. This should be explored
where permissible.
The dangers of an inadequate cleaning cycle are:

• Surface-mounted components are placed in pOSition, but
no solder paste is used. Instead, a drop of adhesive about
5 mils maximum in height with diameter not exceeding
25% width of the package is used to hold down the package. The adhesive is cured and then proceeded to autoinsertion on the reverse side of the board (surface-mounted side facing down). The assembly is then passed over a
"dual wave" soldering system. Note that the surfacemounted components are immersed into the molten solder.
Lead trimming will pose a problem after soldering in the
latter case, unless the leads of the insertion components
are pre-trimmed or the board specially designed to localize
certain areas for easy access to the trim blade.

• Ion contamination, where ionic residue left on boards
would cause corrosion to metallic components, affecting
the performance of the board.
• Electro-migration, where ionic residue and moisture present on electrically-biased boards would cause dentritic
growth between close spacing traces on the substrate,
resulting in failures (shorts).

REWORK

The controls required for wave soldering are:

Should there be a need to replace a component or re-align
a previously disturbed component, a hot air system with appropriate orifice masking to protect surrounding components may be used.
When rework is necessary in the field, specially-designed
tweezers that thermally heat the component may be used to
remove it from its site. The replacement can be fluxed at the

• Solder temperature to be 240-260·C. The dwell time of
components under molten solder to be short (preferably
kept under 2 seconds), to prevent damage to most components and semiconductor devices.
• RMA (Rosin Mildly Activated) flux or more aggressive OA
(Organic Acid) flux are applied by either dipping or foam
fluxing on boards prior to preheat and soldering. Cleaning
procedures are also more difficult (aqueous, when OA flux
is used), as the entire board has been treated by flux (unlike solder paste, which is more or less localized). Nonhalide OA fluxes are highly recommended.

Hot-Air Solder Rework Station
MASeK

,,/ 0
,/

RETRACT POSITION

• Preheating of boards is essential to reduce thermal shock
on components. Board should reach a temperature of
about 1OO'C just before entering the solder wave.
• Due to the closer lead spacings (0.050" vs 0.100" for
dual-in-line packages), bridging of traces by solder could
occur. The reduced clearance between packages also
causes "shadowing" of some areas, resulting in poor solder coverage. This is minimized by dual-wave solder systems.

,/

..-"HEAT SHIELD
BOARD ON X-Y TABLE
HDTAIRTL/XXl0026-35

7-20

en

c

Mixed Surface Mount and Lead Insertion

iiI-

ADHESIVE

(')

CD

R/\
(a) Same Side

-

3:
oc

::s

(b) OpPosite Sides

tttt
PREHEAT

SOLDER FLOW
TL/XX/0026-37

A typical dual-wave system is illustrated below, showing the
various stages employed. The first wave typically is in turbulence and given a transverse motion (across the motion of
the board). This covers areas where "shadowing" occurs. A
second wave (usually a broad wave) then proceeds to perform the standard soldering. The departing edge from the
solder is such to reduce "icicles," and is still further reduced
by an air knife placed close to the final soldering step. This
air knife will blow off excess solder (still in the fluid stage)
which would otherwise cause shorts (bridging) and solder
bumps.

Dual Wave

AQUEOUS CLEANING
• For volume production, a conveyorized system is often
used with a heated recirculating spray wash (water temperature 130·C), a final spray rinse (water temperature
45-55·C), and a hot (120·C) air/air-knife drying section.
• For low-volume production, the above cleaning can be
done manually, using several water rinses/tanks. Fastdrying solvents, like alcohols that are miscible with water,
are sometimes used to help the drying process.
• Neutralizing agents which will react with the corrosive materials in the flux and produce material readily soluble in
water may be used; the choice depends on the type of flux
used.

TL/XX/OO26-36

CONFORMAL COATING
Conformal coating is recommended for high-reliability PCBs
to provide insulation resistance, as well as protection
against contamination and degradation by moisture.
Requirements:

• Final rinse water should be free from chemicals which are
introduced to maintain the biological purity of the water.
These materials, mostly chlorides, are detrimental to the
assemblies cleaned because they introduce a fresh
amount of ionizable material.

• Complete coating over components and solder jOints.
• Thixotropic material which will not flow under the packages or fill voids, otherwise will introduce stress on solder
joints on expansion.
• Compatibility and possess excellent adhesion with PCB
material/ components.
o Silicones are recommended where permissible in
application.
7-21

,.

SMD Lab Support
Technlque&-l)evelop techniques for handling different
materials and processes in surface mounting.
Equipment-In conjunction with equipment manufacturers,
develop customized equipments to handle high density,
new technology packages developed by National.
In-House Expertise-Availability of in-house expertise on
semiconductor research/development to assist users on
packaging queries.

FUNCTIONS
Demonstration-Introduce first-time users to surfacemounting processes.
Service-Investigate problems experienced by users on
surface mounting.
Reliability Builds-Assemble surface-mounted units for reliability data acquisition.

7-22

l>
ZI

Small Outline (SO) Package
Surface Mounting MethodsParameters and Their
Effect on Product Reliability

National Semiconductor
Application Note 450
Josip Huljev
W. K. Boey

The SO (small outline) package has been developed to
meet customer demand for ever-increasing miniaturization
and component density.

In order to achieve reliability performance comparable to
DIPs-SO packages are designed and built with materials
and processes that effectively compensate for their small
size.

COMPONENT SIZE COMPARISON

I......

C

All SO packages tested on 8S%RA, 8S'C were assembled
on PC conversion boards using vapor-phase reflow soldering. With this approach we are able to measure the effect of
surface mounting methods on reliability of the process. As
illustrated in Figure A no significant difference was detected
between the long term reliability performance of surface
mounted 5.0. packages and the DIP control product for up
to 6000 hours of accelerated 8S%/8S'C testing.

S.O. Package

~

0l::Io
U1

TYPICALLY O.D50" LfADSPACINQ

TLlF/B766-1

Standard DIP Package

SURFACE-MOUNT PROCESS FLOW
The standard process flowcharts for basic surface-mount
operation and mixed-lead insertion/surface-mount operations, are illustrated on the following pages.
Usual variations encountered by users of SO packages are:

----1

~ TYPICALLY O.100~ LEADSPACING

TL/F/B76S-2

Because of its small size, reliability of the product assembled in SO packages needs to be carefully evaluated.
SO packages at National were internally qualified for production under the condition that they be of comparable reliability performance to a standard dual in line package under
all accelerated environmental tests. Figure A is a summary
of accelarated bias moisture test performance on 30V bipolar and ISV CMOS product assembled in SO and DIP (control) packages.

• Single-sided boards, surface-mounted components only.
• Single-sided boards, mixed-lead inserted and surfacemounted components.
o Double-sided boards, surface-mounted components only .
• Double-sided boards, mixed-lead inserted and surfacemounted components.
In consideration of these variations, it became necessary for
users to utilize techniques involving wave soldering and adhesive applications, along with the commonly-used vaporphase solder reflow soldering technique.

PRODUCTION FLOW
Basic Surface-Mount Production Flow

V+ = 15VCMOS
30V BIPOLAR
85%RH/85OC
TEST CONomON
DIP

o

2000

4DOO

,.

6000

TEST TIME (HRS)
TL/F/B766-3

FIGURE A
TL/F/B766-4

7-23

,.
z

C) . - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - - ,
\I)

cc

Thermal stress of the packages during surface-mounting
processing is more severe than during standard DIP PC
board mounting processes. Figure 8 illustrates package
temperature versus wave soldering dwell time for surface
mounted packages (components are immersed into the
molten solder) and the standard DIP wave soldering process. (Only leads of the package are immersed into the molten solder).

Mixed Surface-Mount and Axial-Leaded Insertion
Components Production Flow

SOLDER TEMPERATURE 260"C

o

1 2 3 4 5 6 7

9 10 SEC.

DWELL TIME
TL/F/8766-6

FIGUREB

For an ideal package, the thermal expansion rate of the
encapsulant should match that of the leadframe material in
order for the package to maintain mechanical integrity during the soldering process. Unfortunately, a perfect matchup
of thermal expansion rates with most presently used packaging materials is scarce. The problem lies primarily with the
epoxy compound.
Normally, thermal expansion rates for epoxy encapsulant
and metal lead frame materials are linear and remain fairly
close at temperatures approaching l60·C, Figure C. At lower temperatures the difference in expansion rate of the two
materials is not great enough to cause interface separation.
However, when the package reaches the glass-transition
temperature (Tg) of epoxy (typically l60-l65·C), the thermal expansion rate of the encapsulant increases sharply,
and the material undergoes a transition into a plastic state.
The epoxy begins to expand at a rate three times or more
greater than the metal leadframe, causing a separation at
the interface.

TL/F/8766-5

al

I

100 110 120 130 140 150 160,170 180
Tg

T(OC)
TL/F/8766-26

FIGUREC

7-24

.

l>
When this happens during a conventional wave soldering
process using flux and acid cleaners, process residues and
even solder can enter the cavity created by the separation
and become entrapped when the material cools. These
contaminants can eventually diffuse into the interior of the
package, especially in the presence of moisture. The result
is die contamination, excessive leakage, and even catastrophic failure. Unfortunately, electrical tests performed immediately following soldering may not detect potential flaws.

The basic component-placement systems available are
classified as:
(a) In-line placement

z
A

CI1
Q

-

Fixed placement stations
Boards indexed under head and respective components placed
(b) Sequential placement
-

Most soldering processes involve temperatures ranging up
to 260'C, which far exceeds the glass-transition temperature of epoxy. Clearly, circuit boards containing SMD packages require tighter process controls than those used for
boards populated solely by DIPs.

Either a X-V moving table system or a 9, X-V moving
pickup system used

-Individual components picked and placed onto boards
(c) Simultaneous placement
- Multiple pickup heads
- Whole array of components placed onto the PCB at
the same time
(d) Sequential/simultaneous placement

Figure D is a summary of accelerated bias moisture test
performance on the 30V bipolar process.
Group 1 - Standard DIP package
Group 2 - SO packages vapor-phase reflow soldered on
PC boards
Group 3-6 SO packages wave soldered on PC boards
Group 3 - dwell time 2 seconds
4 - dwell time 4 seconds
5 - dwell time 6 seconds
6 - dwell time 10 seconds

-X-Y moving table, multiple pickup heads system
- Components placed on PCB by successive or simultaneous actuation of pickup heads
The SO package is treated almost the same as surfacemount, passive components requiring correct orientation in
placement on the board.
Pick and Place Action

o
TEST TIME (HRS)
TLfFfB766-7

FIGURED

It is clear based on the data presented that SO packages
soldered onto PC boards with the vapor phase reflow process have the best long term bias moisture performance
and this is comparable to the performance of standard DIP
packages. The key advantage of reflow soldering methods
is the clean environment that minimized the potential for
contamination of surface mounted packages, and is preferred for the surface-mount process.

TLfFfB766-B

BAKE

This is recommended, despite claims made by some solder
paste suppliers that this step be omitted.
The functions of this step are:
• Holds down the solder globules during subsequent reflow
soldering process and prevents expulsion of small solder
balls.
o Acts as an adhesive to hold the components in place during handling between placement to reflow soldering.

When wave soldering is used to surface mount components
on the board, the dwell time of the component under molten
solder should be no more than 4 seconds, preferrably under
2 seconds in order to prevent damage to the component.
Non-Halide, or (organic acid) fluxes are highly recommended.

• Holds components in position when a double-sided surface-mounted board is held upside down going into a vapor-phase reflow soldering operation.

PICK AND PLACE

The choice of automatic (aU generally programmable) pickand-place machines to handle surface mounting has grown
considerably, and their selection is based on individual
needs and degree of sophistication.

• Removes solvents which might otherwise contaminate
other eqUipment.
• Initiates activator cleaning of surfaces to be soldered.
• Prevents moisture absorption.

7-25

•

The process is moreover very simple. The usual schedule is
about 20 minutes in a 65'C-95'C (dependent on solvent
system of solder paste) oven with adequate venting. longer
bake time is not recommended due to the following reasons:

In-Line Conveyorlzed Vapor-Phase Soldering
CONDENSATION

J

• The flux will degrade and affect the characteristics of the
paste.

~
-~""" L

- ---I-BELT---"="=-.:::fJ:!!l:.
1
..----1--

• Solder globules will begin to oxidize and cause solderability problems.
• The paste will creep and after reflow, may leave behind
residues between traces which are difficult to remove and
vulnerable to electro-migration problems.

COILS

COILS
c::::=:::)

LIQUID

REFLOW SOLDERING
There are various methods for reflowing the solder paste,
namely:

IMMERSION HEATER
TUF/B766-9

The question of thermal shock is asked frequently because
of the relatively sharp increase in component temperature
from room temperature to 215'C. SO packages mounted on
representative boards have been tested and have shown
little effect on the integrity of the packages. Various packages, such as cerdips, metal cans and TO-5 cans with glass
seals, have also been tested.

• Hot air reflow
• Infrared heating (furnaces)
• Convectional oven heating
• Vapor-phase reflow soldering
• laser soldering
For SO applications, hot air reflow/infrared furnace may be
used for low-volume production or prototype work, but vapor-phase soldering reflow is more efficient for consistency
and speed. Oven heating is not recommended because of
"hot spots" in the oven and uneven melting may result. laser soldering is more for specialized applications and requires a great amount of investment.

Vapor-Phase Furnace

HOT GAS REFLOW/INFRARED HEATING
A hand-held or table-mount air blower (with appropriate orifice mask) can be used.
The boards are preheated to about 100'C and then subjected to an air jet at about 260'C. This is a slow process and
results may be inconsistent due to various heat-sink properties of passive components.
Use of an infrared furnace is the next step to automating the
concept, except that the heating is promoted by use of IR
lamps or panels. The main objection to this method is that
certain materials may heat up at different rates under IR
radiation and may result in damage to these components
(usually sockets and connectors). This could be minimized
by using far-infrared (non-focused) system.
VAPOR·PHASE REFLOW SOLDERING
Currently the most popular and consistent method, vaporphase soldering utilizes a fluoroinert fluid with excellent
heat-transfer properties to heat up components until the solder paste reflows. The maximum temperature is limited by
the vapor temperature of the fluid.

TL/F/B7BB-10

Batch·Fed Production Vapor·Phase Soldering Unit

The commonly used fluids (supplied by 3M Corp) are:
• FC-70, 215'C vapor (most applications) or FX-38
• FC-71 , 253'C vapor (low-lead or tin-plate)
HTC, Concord, CA, manufactures equipment that utilizes
this technique, with two options:
• Batch systems, where boards are lowered in a basket and
subjected to the vapor from a tank of boiling fluid.
• In-line conveyorized systems, where boards are placed
onto a continuous belt which transports them into a concealed tank where they are subjected to an environment
of hot vapor.
Dwell time in the vapor is generally on the order of 15-30
seconds (depending on the mass of the boards and the
loading density of boards on the belt).

TL/F/B766-11

7-26

:I>
Solder JOints on a SO-14 Package on PCB

Solder Joints on a SO-14 Package oil PCB

f

en
o

TUF/8766-12

TL/F/8766-13

PRINTED CIRCUIT BOARD
The SO package is molded out of clean, thermoset plastic
compound and has no particular compatibility problems with
most printed circuit board substrates.

The typical lithographic "footprints" for SO packages are
illustrated below. Note that the 0.050" lead center-center
spacing is not easily managed by commercially-available air
pressure, hand-held dispensers.

The package can be reliably mounted onto substrates such
as:

Using a stainless-steel, wire-mesh screen stencilled with an
emulsion image of the substrate pads is by far the most
common and well-tried method. The paste is forced through
the screen by a V-shaped plastic squeegee in a sweeping
manner onto the board placed beneath the screen.

• G10 or FR4 glass/resin
• FR5 glass/resin systems for high-temperature
applications

The setup for SO packages has no special requirement
from that required by other surface-mounted, passive components. Recommended working specifications are:

• Polymide boards, also high-temperature
applications
• Ceramic substrates

• Use stainless-steel, wire-mesh screens, #80 or #120,
wire diameter 2.6 mils. Rule of thumb: mesh opening
should be approximately 2.5-5 times larger than the average particle size of paste material.

General requirements for printed circuit boards are:
• Mounting pads should be solder-plated whenever
applicable.

• Use squeegee of Durometer 70.

• Solder masks are commonly used to prevent solder bridging of fine lines during soldering.

o Experimentation with squeegee travel speed is recom-

mended, if available on machine used.

The mask also protects circuits from processing chemical
contamination and corrosion.
If coated over pre-tinned traces, residues may accumulate
at the mask/trace interface during subsequent reflow,
leading to possible reliability failures.

• Use solder paste of mesh 200-325.
• Emulsion thickness of 0.005" usually used to achieve a
solder paste thickness (wet) of about 0.008" typical.

Recommended application of solder resist on bare, clean
traces prior to coating exposed areas with solder.

• Snap-off height of screen should not exceed
damage to screens and minimize distortion.

• Mesh pattern should be 90 degrees, square grid.

General requirements for solder mask:
-

Good pattern resolution.

-

Complete coverage of circuit lines and resistance to
flaking during soldering.

-

Adhesion should be excellent on substrate material to
keep off moisture and chemicals.

-

Compatible with soldering and cleaning requirements.

Va" , to avoid

SOLDER PASTE
Selection of solder paste tends to be confusing, due to numerous formulations available from various manufacturers.
In general, the following guidelines are sufficient to qualify a
particular paste for production:
• Particle sizes (see photographs below). Mesh 325 (approximately 45 microns) should be used for general purposes, while larger (solder globules) particles are preferred for lead less components (LCC). The larger particles
can easily be used for SO packages.

SOLDER PASTE SCREEN PRINTING
With the initial choice of printed circuit lithographic design
and substrate material, the first step in surface mounting is
the application of solder paste.

7-27

•

• Composition, generally 60/40 or 63/37 Sn/Pb. Use 62/36
Sn/Pb with 2% Ag in the presence of Au on the soldering
area. This formulation reduces problems of metal leaching
from soldering pads.

• Uniform particle distribution. Solder globules should be
spherical in shape with uniform diameters and minimum
amount of elongation (visual under 100/200 x magnification). Uneven distribution causes uneven melting and subsequent expulsion of smaller solder balls away from their
proper sites.

• RMA flux system usually used.
• Use paste with aproximately 88-90% solids.

RECOMMENDED SOLDER PADS FOR SO PACKAGES
SO-8, SO-14, SO-16

SO-16L, SO-20

····1oJ.'
L••••
I-

0.045" :t 0.005"

r····~

L••••
J:..
1- -I

0.245"

0.030" :to.005"

0.160"

-..I

o.m"'.

:.':r.

!-0.050"TYP
TL/F/8766-14

SOT-23
0.030" :to.005"1

I

0.030" :to.005"

--l

-I 1-~

TYP

TL/F/8766-15

1·--->-.

"r.-1o:r~~~
TL/F/8766-16

Comparison of Particle SlzelShape of Various Solder Pastes
200 x Alpha (62/36/2)

200 X Kester (63137)

TL/F/8766-17

TUF/8766-18

7-28

Comparison of Particle Size/Shape of Various Solder Pastes (Continued)
200 X Fry Metal (63/37)

Solder Paste Screen on Pads

TL/F/B766-20

TLlF/B766-19

200 ESL (63/37)

TLlF/B76B-21

7-29

CLEANING

Hot-Air Rework Machine

The most critical process in surface mounting SO packages
Is in the cleaning cycle. The package is mounted very close
to the surface of the substrate and has a tendency to collect
residue left behind after reflow soldering.
Important considerations in cleaning are:
• Time between soldering and cleaning to be as short as
possible. Residue should not be allowed to solidify on the
substrate for long periods of time, making it difficult to
dislodge.
• A low surface tension solvent (high penetration) should be
employed. Solvents commercially available are:
Freon TMS (general purpose)
Freon TE35/TP35 (cold-dip cleaning)
Freon TES (general purpose)

TlIF/8788-23

lead tips or, if necessary, solder paste can be dispensed
onto the pads using a varimeter. After being placed into
position, the solder is reflowed by a hot-air jet or even a
standard soldering iron.

It should also be noted that these solvents generally will
leave the substrate surface hydrophobic (moisture repellent), which is desirable.

WAVE SOLDERING

Prelete or 1,1,1-Trichloroethane
Kester 5120/5121

In a case where lead insertions are made on the same
board as surface-mounted components, there is a need to
include a wave-SOldering operation in the process flow.

• A defluxer system which allows the workpiece to be subjected to a solvent vapor, followed by a rinse in pure solvent and a high-pressure spray lance are the basic requirments for low-volume production.
• For volume production, a conveyorized, multiple hot solvent spray/jet system is recommended.
• Rosin, being a natural occurring material, is not readily
soluble in solvents, and has long been a stumbling block
to the cleaning process. In recent developments, synthetic flux (SA flux), which is readily soluble in Freon TMS
solvent, has been developed. This should be explored
where permissible.
The dangers of an inadequate cleaning cycle are:

Two options are used:
• Surface mounted components are placed and vapor
phase reflowed before auto-insertion of remaining components. The board is carried over a standard wave-solder
system and the underside of the board (only lead-inserted
leads) soldered.

• Ion contamination, where ionic residue left on boards
would cause corrosion to metallic components, affecting
the performance of the board.
• Electro-migration, where ionic residue and moisture present on electrically-biased boards would cause dentritic
growth between close spacing traces on the substrate,
resulting in failures (shorts).

REWORK
Should there be a need to replace a component or re-align
a previously disturbed component, a hot air system with appropriate orifice masking to protect surrounding components may be used.
When rework is necessary in the field, specially-designed
tweezers that thermally heat the component may be used to
remove it from its site. The replacement can be fluxed at the
Hot-Air Solder Rework Station
MASeK

//' 0

RETRACT POSITION

---01;""------.
,

----

• RMA (Rosin Mildly Activated) flux or more aggressive OA
(Organic Acid) flux are applied by either dipping or foam
fluxing on boards prior to preheat and soldering. Cleaning
procedures are also more difficult (aqueous, when OA flux
is used), as the entire board has been treated by flux (unlike solder paste, which is more or less localized). Nonhalide OA fluxes are highly recommended.

• Due to the closer lead spacings (0.050' vs 0.100· for
dual-in-line packages), bridging of traces by solder could
occur. The reduced clearance between packages also
causes "shadowing" of some areas, resulting in poor solder coverage. This is minimized by dual-wave solder systems.

HEAT SHIELD
BOARD ON

• Solder temperature to be 240-260·C. The dwell time of
components under molten solder to be short (preferably
kept under 2 seconds), to prevent damage to most components and semiconductor devices.

• Preheating of boards is essential to reduce thermal shock
on components. Board should reach a temperature of
about 100·C just before entering the solder wave.

,/
,/

• Surface-mounted components are placed in position, but
no solder paste is used. Instead, a drop of adhesive about
5 mils maximum in height with diameter not exceeding
25% width of the package is used to hold down the package. The adhesive is cured and then proceeded to autoinsertion on the reverse side of the board (surface-mounted side facing down). The assembly is then passed over a
"dual wave" soldering system. Note that the surfacemounted components are immersed into the molten solder.
Lead trimming will pose a problem after soldering in the
latter case, unless the leads of the insertion components
are pre-trimmed or the board specially designed to localize
certain areas for easy access to the trim blade.
The controls required for wave soldering are:

x-v TABLE

HOT AIRTL/F/8766-22

7-30

.----------------------------------------------------------------.~

z

Mixed Surface Mount and Lead Insertion

•

"'enc"

ADHESIVE

/\

!Ch€:y ~ F=\
(a) Same Side

CZ'M

(b) Opposite Sides

tttt
PREHEAT

SOLDER FLOW
TL/F/8766-24

A typical dual-wave system is illustrated below, showing the

Dual Wave

various stages employed. The first wave typically is in turbulence and given a transverse motion (across the motion of
the board). This covers areas where "shadowing" occurs. A
second wave (usually a broad wave) then proceeds to perform the standard soldering. The departing edge from the
solder is such to reduce "icicles," and is still further reduced
by an air knife placed close to the final soldering step. This
air knife will blow off excess solder (still in the fluid stage)
which would otherwise cause shorts (bridging) and solder
bumps.
AQUEOUS CLEANING
• For volume production, a conveyorized system is often
used with a heated recirculating spray wash (water temperature 130'C), a final spray rinse (water temperature
45-55'C), and a hot (120'C) air/air-knife drying section.
• For low-volume production, the above cleaning can be
done manually, using several water rinses/tanks. Fastdrying solvents, like alcohols that are miscible with water,
are sometimes used to help the drying process.
• Neutralizing agents which will react with the corrosive materials in the flux and produce material readily soluble in
water may be used; the choice depends on the type of flux
used.
• Final rinse water should be free from chemicals which are
introduced to maintain the biological purity of the water.
These materials, mostly chlorides, are detrimental to the
assemblies cleaned because they introduce a fresh
amount of ionizable material.

TLlF/8766-25

CONFORMAL COATING
Conformal coating is recommended for high-reliability PCBs
to provide insulation resistance, as well as protection
against contamination and degradation by moisture.
Requirements:
• Complete coating over components and solder joints.
• Thixotropic material which will not flow under the packages or fill voids, otherwise will introduce stress on solder
joints on expansion.
• Compatibility and possess excellent adhesion with PCB
material/components.
• Silicones are recommended where permissible in
application.

7-31

•

Q
Ln

~

CC

r-----------------------------------------------------------SMD Lab Support
FUNCTIONS
Demonstration-Introduce first-time users to surfacemounting processes.
Service-Investigate problems experienced by users on
surface mounting.
Reliability Builds-Assemble surface-mounted units for reliability data acquisition.

Techniques-Develop techniques for handling different
materials and processes in surface mounting.
Equipment-In conjunction with equipment manufacturers.
develop customized equipments to handle high density.
new technology packages developed by National.
In-House Expertise-Availability of in-house expertise on
semiconductor research/development to assist users on
packaging queries.

7-32

Section 8
Appendicesl
Physical Dimensions

Section 8 Contents
Appendix A General Product Marking and Code Explanation .............................
Appendix B Devicel Application Literature Cross-Reference. . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Appendix C Summary of Commercial Reliability Programs ...... " ...... .. . . .... ... .. ....
Appendix D Military Aerospace Programs from National Semiconductor ........•..........
Appendix E Understanding Integrated Circuit Package Power Capabilities. . . . . . . . . . . . . . . . . .
Appendix F How to Get the Right Information from a Datasheet. . . . . . . . . . . . . . . . . . . . . . . . . . .
Appendix G Obsolete Product Replacement Guide. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Appendix H Safe Operating Areas for Peripheral Drivers. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
PhYSical Dimensions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Bookshelf
Distributors

8-2

8-3
8-4
8-11
8-13
8-22
8-27
8-31
8-33
8-41

~National

~ Semiconductor

Appendix A
General Product Marking & Code Explanation
LF

11
356

N

IA+

I

Package Type

""""""(Refer
Pro,~to Appendix
,0"",0.)C)

GlasslMetal DIP
Ceramic Leadless Chip Carrier (LCG)
GlasslMetal Flat Pak (%" x %n)
12 Lead TO-S Metal Can (M/C)
Multi-Lead Metal Can (MIG)
4 Lead MIC (TO-5) } Shipped with
4 Lead MIC (TO-46)
Thermal Shield
J
La-Temp Ceramic DIP
J-8
8 Lead Ceramic DIP ("Mini DIP")
14 Lead Ceramic DIP (-14 used only when
J-14
product is also available in -8 pkg).
K
T0-3 MIC in Steel, except LM309K
which is shipped in Aluminum
KC
TO-3 MIC (Aluminum)
KSteel TO-3 MIC (Steel)
M
Small Outline Package
3-Lead Small Outline Package
M3
Molded DIP (EPOXY B)
N
N-01
Molded DIP (Epoxy B) with Staggered Leads
N-8
8 Lead Molded DIP (Epoxy B) ("Mini-DIP")
N-14 14 Lead Molded DIP (Epoxy B)
(-14 used only when product is also
available in -8 pkg).
P
3 Lead TO-202 Power Pkg
Q
Cerdip with UV Window
3,5,11,15 & 23 Lead TO-220 PWR Pkg (Epoxy B)
T
V
Multi-lead Plastic Chip Carrier (PCC)
Lo-Temp Ceramic Flat Pak
W
WM
Wide Body Small Outline Package
0
E
F
G
H
H-05
H-46

Package Type (See Right)
Device Number (Generic Type)
and Suffix Letter (Optional)
A or B: Improved
Electrical
Specification
C, I, E or M: Temperature
Range
Device Family (See Below)

Device Family
ADC
AF
AH
DAC
OM
HS
LF
LH
LM
LMC
LMD
LP
LPC
MF
LMF

Data Conversion
Active Filter
Analog Switch (Hybrid)
Data Conversion
Digital (Monolithic)
Hybrid
Linear (Bifet)
Linear (Hybrid)
Linear (Monolithic)
Linear CMOS
LinearDMOS
Linear (Low Power)
Linear CMOS (Low Power)
Linear (Monolithic Filter)
Linear Monolithic Filter

DATE CODE
1ST DIGIT - CALENDAR YEAR
2ND DIGIT - 6-WEEK PERIOD
IN CALENDAR YEAR
3RD 8: 4TH DIGITS - WAFER LOT CODE

DATE CODE
NON-MILITARY
2ND DIGIT - CALENDAR YEAR
3RU 4TH DIGITS - CALENDAR WORK WEEK
MILITARY - 883! M38510
1ST! 2ND DIGITS-CALENDAR YEAR
3RD &4TH DIGITS - CALENDAR WORK WEEK
(EXAMPLE: 9201 =1ST WEEK Of 1992)

INDICATES PLANT
Of MANUfACTURE

MILITARY ONLY
ESD
(ELECTROSTATIC DISCHARGE)
SENSITIVITY INDICATOR

INDICATES PLANT
OF MANUFACTURE

LOGO
PART NUMBER
PIN 1 ORIENTATION

TUXX/OO27-3
TUXX/0027 -2

PIN 1 ORIENTATION

8-3

•

~National

~ Semiconductor

Appendix B
Device/ Application Literature Cross-Reference
Device Number

Application Literature

ADCXXXX .................................................................................................AN-156
ADC80 ...................................................................................................AN-360
ADC0801 .................................................... AN-233, AN-271 , AN-274, AN-280, AN-281, AN-294, LB-53
ADC0802 ................................................................... AN-233, AN-274, AN-280, AN-281, LB-53
ADC0803 ................................................................... AN-233, AN-274, AN-280, AN-281, LB-53
ADC08031 ................................................................................................AN-460
ADC0804 ............................................ AN-233, AN-274, AN-276, AN-280, AN-281, AN-301 , AN-460, LB-53
ADC0805 ................................................................... AN-233, AN-274, AN-280, AN-281 , LB-53
ADC0808 ..................................................................................AN-247, AN-280, AN-281
ADC0809 ......................................................... ',' .............................. AN-247, AN-280
ADC0816 ..........................................................................AN-193, AN-247, AN-258, AN-280
ADC0817 ..................................................................................AN-247, AN-258, AN-280
ADC0820 .................................................................................................AN-237
ADC0831 ............................... : ..........................................................AN-280, AN-281
ADC0832 .........................................................................................AN-280,AN-281
ADC0833 .........................................................................................AN-280, AN-281
ADC0834 .....•..................................................................... ; ............. AN-280, AN-281
ADC0838 .........................................................................................AN-280, AN-281
ADC100l ..................................................................................AN-276, AN-280, AN-281
ADC1005 ....•........•...........................................................•..........•..•.........AN-280
ADC10461 ................................................................................................AN-769
ADC10462 ...•............................................................................................AN-769
ADC10464 ...•.............•..............•..................................................•.......•....AN-769
ADC10662 ...•................•.................•.......................... ,..................•....••...... AN-769
ADC10664 ..............................................................' ................................... AN-769
ADC1210 ....•....................................................................•......••..........•.•..AN-245
ADC12441 .........•......................................................................................AN-769
ADC12451 ................................................................................................AN-769
ADC3501 .........................................................................................AN-200,AN-202
ADC3511 .................................................................................................AN-200
ADC3701 .................................................................................................AN-200
ADC3711 .................................................................................................AN-200
AH0014 ....................................................................................................AN-38
AH0019 ....................................................................................................AN-38
CD4016 ....................................................................................................AB-l0
DACXXXX .......................................................... , ................•............•........ AN-156
DAC0800 .............................................................................•..................•AN-693
DAC0830 ................................................. , ............................................... AN-284
DAC0831 .........................................................................................AN-271,AN-284
DAC0832 .........................................................................................AN-271, AN-284
DAC1000 ..........................................................................AN-271 , AN-275, AN-277, AN-284
DAC100l ..........................................................................AN-271 , AN-275, AN-277, AN-284
DAC1002 ..........................................................................AN-271, AN-275, AN-277, AN-284
8-4

Device!Application Literature Cross-Reference (Continued)
Device Number

Application Literature

DAC1 006 •••.••.•.•.••.•••••..•.•..•......•..............................•••••.••.• AN·271 , AN·275, AN·277, AN·2B4
DAC1 007 ..........................•.........•••..•.•••.•.••.•.•..•................ AN·271 , AN·275, AN·277, AN·2B4
DAC100B .••.••••.....•............•.............•...••.••••.••••..••••.•••....•... AN·271 , AN·275, AN·277, AN·2B4
DAC1020 ..................••.•.•.••.•.•....•.............................AN·263, AN·269, AN·2293, AN·294, AN·299
DAC1021 •..•.•••••.•.......•...........................................••••...•.•••.•.••....•.....•.••... AN·269
DAC1022 .................................................................................................AN·269
DAC120B •.•..•.••••••.•.•..•.•.....•..............................•.....••••...•••..•..•...•••••• AN·271 , AN·2B4
DAC1209 ...........................•.••.•.•••.•.•••.....••..•........•...........................AN·271 , AN·2B4
DAC1210 ....••.....•...........•...••••.••.•••••••••••••••.••...•..•............................. AN·271,AN·2B4
DAC121B .................................................................................................AN·293
DAC1219 .................................................................................................AN·693
DAC1220 .................••••••••••••••.•••••.•.•................................................ AN·253, AN·269
DAC1221 .•.••••.•..•.••...........•.....•...•....••••.••••••••.•.••.••...•....................•.......... AN·269
DAC1222 •..••••.••.•.•.••...••••..•......•....•.....•...•.••••.•••.•••••••.••.••••.•••.•.••••••..•.••.... AN·269
DAC1230 .................•...•...•••••.•••.•••••.........................................................AN·2B4
DAC1231 ......•........•••.•••••.••..•.....•.........................•...........••.•.•.••......• AN·271 , AN·2B4
DAC1232 ................•................•.••••••••..•.........•.................................AN·271 , AN·2B4
DAC12BO •.•..••••..•••...•..•.•............•.............•.•..•••.••.••.•••••.•••••.••••.•.•.•••• AN·261 , AN·263
DH0034 .................•.............•.•••••••••.•••.••.•..•.......•.....................................AN·253
DH0035 ...••.••••.•••.....•.•...•...•..............••.•••••••••••••.••••••••••.•.•.••••.••.•.•..•..•....... AN·49
Digitalker ...................•.••..••..••.•••••.••.•..•..............................................AN·252, LB·54
DMBB90 .••.•.•••••.•••.•..•..•...••.................•..•...••••.•••••••.••••.••••.•.•...•.•••.•.....•. Appendix B
DSB606 ..................•.•.••••.••••••.•••••••••••.•••.............................•............ AN·3B1,AN·3B2
DSB60B ••.•.•••.••...•..•.••..•...................•.••.••••••.•••.•••••.•••.••••..........•...•.........•. AN·3B2
DT105B •••.••••.••••.••••••••••••..•.••.•.....................•..•.•.•..••..•••••••••••••••••••.•••.•..••• AN·2B7
DT1 060 •.................••..•.•••••••••••••••••••••••.••••.•••.••••••..•...•..•.......................... AN·2B7
DTSW250E2 ••.•.••••.•••.•...•.•..•...•......•....•....................•..•.•••••.•.•••••.••••••..••...•• AN·2B7
DTSW250GI ..................•..•...•.•••.••.••••••••.•••••••••...•••......•.............................. AN·2B7
INSB070 ............................................ : ...................................................... AN·260
LF111 ••••.••••••••••••••...••....•...•...•............•..••.••••.•••••.•••••••••••••••••••..••••••••••..•.• LB·39
LF155 •..•.........•.•.•••••••••••.••••.••.••••••••.•..•..•...••.................................. AN·263,AN·447
LF19B ..•......•.••.................•.....••...•...•..••.••••.•••••.•.•••••..••••••••••.•••••••••• AN·245, AN·294
LF311 •...•••....•...•••••.••••••••••••••••••....•.••.............•..........•..........................•. AN·301
LF347 .•.....•.................•...•..•..•... AN·256, AN·262, AN·263, AN·265, AN·266, AN·301, AN·344, AN·447, LB·44
LF351 ••.••••.••••.•.••.•.••••••••••.••••••...•. AN·242, AN·263, AN·266, AN·271, AN·275, AN·293, AN·447, Appendix C
LF351A ........................••.••.•••••••••••••••••••.••..•...••...•...•...•.....................•..... AN·240
LF351B •.•..••.••••••••••.••••.....•..............•....•••••••.••••••.•.•.•..•••••••••••.•••••••.•.••• AppendixD
LF353 •.....•..•.. AN·256, AN·25B, AN·262, AN·263, AN·264, AN·266, AN·271, AN·2B5, AN·293, AN·447, LB·44, Appendix D
LF356 .......•.....•...............•...•..•.••••.•••••••••• AN·253, AN·25B, AN·260, AN·263, AN·266, AN·271, AN·272,
AN·275, AN·293, AN·294, AN·295, AN·301, AN·447, AN·693
LF357 ............•..•••.•.•.•••••.•••••••••••••••....•••.••.....•..............•..•...•.... AN·263, AN-447, LB-42
LF39B ..•.•....•............•.....••....•.....•••••••••••••••••••••.• AN·247, AN·25B, AN·266,'AN·294, AN·29B, LB-45
LF400 ••••••.••••.••••.•••••.•••.•••••••••..•.•.•.••...•..••••••.•••.••••••••.•••••.•••••.•••••.•• AN·42B, AN·447
LF411 •••..••••••••••••••.••••••.••••••••••••••••••••••••••••••••.•.....•...•....•. AN·294, AN·301, AN·344, AN·447
LF412 •.........••.....•.••••.••••••••••.•••••••••.••••••••••.•••...•.••..• AN·272, AN·299, AN·301, AN·344, AN·447
LF441 ••••••••••••••...••••••••••••...•.•..•...••..•.•...•....•.......•..........•................ AN·301, AN-447
LF13006 •.••••••••••••••••.•••..•••••..••...•.....••••..••••••••••••••••••••••••••.•••••••••••••••.••••••. AN·344
LF13007 •.•••••••••.••••••.•.••••••••.••••••••••.•.•......•.••...........•..•..•••.•....•.•.•....•...••••. AN·344
LF13331 ••.•..••.••••.•••••••••••••••••••••••••••••••••••••..•••••.••••...••.....•.....•.......... AN·294, AN-447
LF1350B •..•.••......•....•..•...•...•......••.••••••••••.•.•••.•••.•.••••••••.•••••••••.• AN·2B9, AN·3BO, AN·447
LF13509 •••••••••.••••••••••••.•••.•.••••.•.....••...•.......•........•.•......•.•••••••.• AN·2B9, AN·295, AN·447
B·5

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,-----------------------------------------------------------------------------.
DevicelApplication Literature Cross-Reference (Continued)

Q;

Device Number

a:

Application Literature

~

LH0005 .............••••••.•.••...•.............•...••.••••••.••••.••.••.•••••••••.•••••..••••.•......•.... AN·13

o

LH0022 ••.•......•.........•....••••••••••.••••..•....•••....•••.•••..•••.......••.........•......•• AN·63, AN·75

~

LH0023 •.•.••...........•.....•.••.••••••••••••••..•.•....••.•.•....•••.........•...•.•.......••.. AN·245, AN·360

1!

LH0032 ..........•.............••••.•••••••.•..............•...........•....•....•........ AN·242, AN·244, AN·253

~

LH0002 •.•••.•.••..................••.••••••••••••....•....•• AN·13, AN·63, AN·227, AN·244, AN·263, AN·272, AN·301

LH0024 .........•..•.••••........................•....•••...•••••••••••••••••••••••.•••..••.•....•....... AN-253

~

LH0033 ....•••••..•.••..•.............•..•..•.•.••••••.•••••••.••••••.••.••••.••••• AN-48, AN·115, AN·227, AN·253

o

LH0042 ................•••.••........................•.........•...•••..•••.•••••..••••.••••••••.•.•.•.....AN·63
LH0043 ............•.........••.•.•.•••.•.....••.........•.........•.....•...............•••.•••.••.•••••• AN·245

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LH0052 ......•••.•••••.••....•..............•...•.•••.•••••••••••••••••••••••••••••••••.•.•••.••........... AN·63
LH0053 ............•..••••••••....•..•..•..............•........•..•.....•....••••••••••••••.••••••.•••.•• AN·245
LH0062 .................•....•••••••••••••....•..•.••...•..•...•...•••....•....•.........•••.•.•••••••.•••• AN·75
LH0063 ..••••••.••••••••................•..•..•••••••••••••..••••••••••.••••••••••••••••••••..•...•....... AN·227
LH0070 ...•......•.••.•••••••.•••..•....•...................•..•••.••.•••••••••..•••••.•••••..••.••..••.•. AN·301
LH007l .............................••••••.•.•••....•••.............•........•.....•................••.•••AN·245
LH0082 .......•..•••.•••••.......•..................•.....••.....••.•....••••.••••.••••••••••••••• AN·244, AN·266
LH0086 ......................•••••.•••••••.••.••..••.•.•...••.••••....•.•......•.••..••....•....••AN-245,AN-360
LH009l ..••••••.•.•••.••..............•.•..•....•••••.•.•.•..••••••••••.•••.••••••••••.•••••.••.•..•...... AN-180
LH0094 ..................••.••••••••••.•••.•••••..•.•..•.••.•....•••.•••.•..•.••.•.•......•...•...••••••.• AN-30l
LH010l ..............•.••.••••••••••••.•..••••.•••..••.••.•...•.......••••.......•.•.......••••••.•••.•..• AN-26l
LH1605 •••••••.•••..................•..............••..••••.•••••••.•••.••••••••••••••.••••••••...••.••... AN-343
LM10 .....................•.••••••••••••••• AN-2ll, AN-247, AN-258, AN-27l, AN-288, AN-299, AN-300, AN-460, AN·693
LM11 •..••••.•••.•.•...•.••...............•..........•....•••.••••.•••••..• AN-24l, AN-242, AN-280, AN-266, AN-27l
LM12 ................••••••••••.••••.•••.••.••.•.....•......•....•••....•....•....•....... AN-446, AN-693, AN-706
LM10l .......................................................... AN-4, AN-13, AN-20, AN-24, AN-75, LB-42, Appendix A
LM101A .................. AN-29, AN-30, AN-3l , AN-79, AN-24l AN-7ll, LB-l, LB-2, LB-4, LB-B, LB-14, LB-16, LB-19, LB-28
LM102 ..................................................................AN-4,AN-13,AN-30, LB-l, LB-5, LB-6, LB-11
LM103 •••••••••••••••..•.•.........••.............•.•...•.........•.•.....•....•...••••.•••••.••••• AN-ll0,LB-4l
LM104 •...........•..........•..•...••••••••••••••••••••••••.•••.•••••.••••••.•••••• AN-2l, LB-3, LB-7, LB-l0, LB-40
LM105 .....................................................................AN-21,AN-23,AN-1l0, LB-3, LB-7, LB-l0
LM106 .......•••.•••••.•••••...•..•.•....•.......•.......•........•......•....•.•.............•AN-4l, LB-6, LB-12
LM107 .......•......................•.••....•..••••.•••.•.•.••.•••••.•• AN-20, AN-31 , LB-1, LB-12, LB-19, Appendix A
LM108 ..•..•..•..•••••••••......•••.......... AN-29, AN-30, AN-31 , AN-63, AN-79, AN-211, AN-241 , LB-14, LB-15, LB-21
LM108A .........•................•..•..•.•••••.•.••••••••..•••.••••••••.••••••••••••.••••.••. AN-260, LB-15, LB-19
LM109 ....••••••.•.••••.•••••....•....•.............•.•...•....••......•.•....•..•.................•AN-42, LB-15
LM109A ...............••..••••••••••••••••..•.••••••••.•.•....••.•••••.••.••.•.......•...•...•............. LB-15
LM110 .•.....•......................•.•............•.....••.....•.....•....•....•...•••.••••••••••••• LB-11, LB-42
LM111 •............•..•.•.•••..••••.••••..•...•••..•..••.•...•.•.....•.•.• AN-41,AN-103, LB-12, LB-16, LB-32, LB-39
LMl12 ...•.........•.............•...••..•••....••..•..•...•••••.....••.•.•••..•••....••••••••.•••••AN-63,LB-19
LM113 .....•.••...•.••••••.•..•....•..••.....•........••.....•....•....... AN-56,AN-110, LB-21 , LB-24, LB-28, LB-37
LM1l7 .......................................................................AN-178, AN-181, AN-182, LB-46, LB-47
LM1l7HV ......................•..........•...............•......•...•....•....•.•...••....••...••••• LB-46, LB-47
LM118 ...•.•.•••.••••••.•••.•.•.•••..•..........••.......•.•.•.•.••.•..•...•. LB-17, LB-19, LB-21 , LB-23, Appendix A
LM119 ..............•...................•.......•...•.....••...•.....•......•.........•....•••.••••AN-115, LB-23
LM120 •.•.•....••.....•.........•...•......•...•..........•........•.•.•.....•.•....•.••.....•.......•.... AN-182
LM121 .....................•.....•...•••..•••..•.•.•....•..•..•.•....•.••...• AN-79, AN-1 04, AN-184, AN-260, LB-22
LM121A ............•..........•....•••...•.••.•••••.•...•••••.••.••.•••..•••.....•..•••.•••••••••••••.•••.. LB-32
LM122 .......•..•..••.•....•.....•.........................•........•.............•........•......•.AN-97, LB-38
LM125 .........•..........•••.•••••.••••••••••••••.•••••.••••••••••.•••••.••••.•••.•••••••••...••••..••.... AN-B2
LM126 .......•.......................•..............•......•............•.......•.•...•......•..•.•........AN-82

8-6

DevicelApplication Literature Cross-Reference (Continued)
Device Number

Application Literature

LM129 ............................................................................AN-173, AN-178, AN-262, AN-266
LM131 .................................................................................AN-210, AN-460, Appendix D
LM131A ..........................•...........•......•.........•...............••......•.•.•••....••.•.•.•AN-210
LM134 ............................................................................................. LB-41,AN-460
LM135 ....................................................................AN-225, AN-262, AN-292, AN-298, AN-460
LM137 ....•.•••.•.••••...•.•.•••.•.••••.••••.•.•.•.•••••..•••.•.•..•.•••.••••••.•.•.•.•.•.•••....••.•.•.... LB-46
LM137HV ..................................................................................................LB-46
LM138 ..•.•.•........•..••••...•.•.•.•.•••••••.•.•.•.•••.•.•...••...•••••.•.•.••.•.•.••.....•.•.•.•.•....•. LB-46
LM139 ••••••..•• , •..•••••.••••..••••.• " ...••••••••...•.••...•.•.••.•.•.••.•.•.•.•.•.•.•.•...•.•..••.....•. AN-74
LM143 ............................................................................................AN-127, AN-271
LM148 .••••.•.•.•.•.•.••••...•..••.•.•.•.••.•....••..••.••.•.•....•.•.•.•.....••.•••.•....•.••..•...•..••• AN-260
LM150 .•.•••.•.•••...•.•.••••.••••.••••.•.••.•..••••••••..•.•.•.•..•••••..•••••.•.•.•.•.•.•...•..••.•.•...• LB-46
LM158 ....................................................................................................AN-116
LM160 .••.•.•.•.•.•.•••••..•••.•.•••.•.••..•.•.•.•••...•••.•.•.•.••.•.•••.•...••.•.••••.••..••••..•••.••.•. AN-87
LM161 .............................................................................................AN-87,AN-266
LM163 ••.•••..•••.•..•••.•••...••••••••••.••••.•••••.•••.•.••••.••••...••.•.•.•..••••.•.•••.•.•...•••.•.•• AN-295
LM194 .............................................................................................AN-222, LB-21
LM195 ....................................................................................................AN-110
LM199 .••••...•••.•.•••.•.•...••••••.•.••••••.•••••..••.•.•••••.•••••••.••.•.•••.•••.•..•• AN-161,AN-260, AN-360
LM199A .••••..•••.•.•••.••••.•.•.•••••••.•••••.•.•••••••••.•.•.••.•.•••••••.••••.•.•.•.•.•••••..•.••••.•. AN-161
LM211 .....................................................................................................LB-39
LM216A .................................................................................................... LB-37
LM231 ••.•.•.•.•••••••••.••••....•.••.•••.••••••.•.•••.•••.••••.•.••..•••••.••.•.••••.•.•• , .•..•..•••.•••. AN-210
LM231A .•.•.•.•••.•.•.•.••••.•.•••.•.•••.••••..••.•.•••••.••••...•.•.•••.•.•••.•••••.•.•••...••..•••...•• AN-210
LM235 .••.•••.•.•••.•••••..•••.•••••••••.•.••••.•••.•••••.•.•.••••.•••••.•.•.••...•••...••••••...•.•••..•• AN-225
LM239 •••.••••..•••••..•••.•••..••.•.•.••..••••••••••.•.••••.•.•.••.•.•.••••.•••.•.•••.•••.•.•.•.•.•.•.•••. AN-74
LM258 •••.•••.•••••.•••••.••••.•••••••••.•.••.•.•••.•.•••.•.••••••.•••••.•.•.••.•.•.•.•.•.•••••..•.••••.•. AN-116
LM260 ••.•••••.•••••••••••••.•••.•.•••.••.••.••••••••.•.••••.•.•.••.•.••••••.•.•..••••.•••.•...•••.•.•.•••• AN-87
LM261 ••••.•.•••••••.••••.•••••..••••.•••.•.•.•.••.•.•.••••.•.•.•.••••.••.•.•.•••.•••••.•.•••••...•••.•..•• AN-87
LM34 ••..•......•..•.•••..........•.•••......•...•••........•••..••........•••.•.........•...•.•..••.•.•.• AN-460
LM35 ••.••.•.•.•••.•.•.•.•••....••••.•.••.••••.•.•••..••••••••..•••.•.•.••••.•••...•••.•.•••.•.•.•..••.•.• AN-460
LM301A ...................................................................................AN-178, AN-181, AN-222
LM304 •••.•.•.•.•...••..•.•....•••..••••.••••.•.••...••••.•.•....•.•.•.•••..•...•••••..•..••.•..•.••..••.•. LB-40
LM308 ............................................................. AN-88, AN-184, AN-272, LB-22, LB:28, Appendix D
LM308A ............................................................................................AN-225, LB-24
LM309 ............................................................................................AN-178,AN-182
LM311 ..•••••.•••...•••..•• AN-41, AN-103, AN-260, AN-263, AN-288, AN-294, AN-295, AN-307, LB-12, LB-16, LB-18, LB-39
LM313 ....................................................................................................AN-263
LM316 ....................................................................................................AN-258
LM317 ••••....••...•••••••.•.•••.•.•.•.••••••.•••••.•••...•••.•••..•••••.••.••••••••.•••.•.•• AN-178, LB-35, LB-46
LM317H ..•.•••••••.•••••.••••.•••••••••.•.••••.••••••.•.••••••.•.•..••••.•••.••••.•.•.•.•.•.........•.•.•.• LB-47
LM318 ......................................................................................AN-115,AN-299, LB-21
LM319 ••••.•..••.•.•.•.•.•••...•••.•••••••••••.••.•.•.....••••••.•....••.••••••••..•.••••• AN-115,AN-271,AN-293
LM320 •..•••...•••.•..••.••••.•.•••.•••••.••••.•••••..••••.•.•.•.••••.•••••••••.•.•.•••.•.•••....••••.•.•. AN-288
LM321 ..•.•.•.•••.•••.•.•.•.•.••••..•••...•.••••.•.•.•.•....••••....•.•.••.••.•...•••.•....•••••.•.•....... LB-24
LM324 .••.•••.•.••..•.•••..•..••.•.•..•••.•.•.••••• AN-88, AN-258, AN-274, AN-284, AN-301, LB-44, AB-25, Appendix C
LM329 .•.••••.•.•••••.•••....•.•.•.••••••••••••••••••..•..•.•••••.•...•.•• AN-256, AN-263, AN-284, AN-295, AN-301
LM329B •.•••.•••••.••••••••••.•••••••••.••••••.••.•••.•.••••.•.•••.•.•.••••.•.•..•••...•••••.••.•.••••••• AN-225
LM330 •••.•••.•••••.•••••..•••.•••••••••.••••••.•••.••.•.••••••..••.•.•.•••.......•••.••••••.. " .•........ AN-301
LM331 •••..••..•.•....•.•.••••....•.•. AN-210, AN-240, AN-265, AN-278, AN-285, AN-311, LB-45, Appendix C, Appendix D
LM331A •••......•.•..•••.....•••.•.•••..•.•.••••••••••.•.••••.•••.•.•.•..••••••••.•.•.•.•.•••. AN-210,AppendixC
8-7

Device/Application Literature Cross-Reference (Continued)
Device Number

Application Literature

LM334 ••••••••••.........•............•.............••.........•....................••.... AN-242, AN-256, AN-284
LM335 ..........••••••.....•.•••..•....•..•...........•.•.•.•.•.........••.............•••AN-225, AN-263, AN-295
LM336 ..••.•..••.......••............•....•...•.•..•••........•.••.••....•..........••...•AN-202, AN-247, AN-258
LM337 ••.••.••.••.•....•.•.....................................•.•..••...............•............•........ LB-46
LM338 ........•.•••••••.....•••••...•..•.••••.........••.•..•.•.......•••••.•..........•••.••.••.•.•. LB-49, LB-5l
LM339 ...•..•.....................................••.•.........•..•..................•.....AN-74, AN-245, AN-274
LM340 ...........•••... , ..••••.........•••............•.................•...........•...•.•.......AN-l03, AN-182
LM340L. •.......•....••..............••....•.••••...........•.•....•..•.........••..•.....•...•.•..•...... AN-256
LM342 .•.••••.•..........•................•.......•.•••...............•..........•..•.....................AN-288
LM346 •............•.•......•..•••.....•..••••..........•....•...•.....•..............••.•..•••.•.. AN-202, LB-54
LM348 ..••..•..........................•.....•....•.••...........•..•..............•.•.......•.....AN-202, LB-42
LM349 •.......••..••..•..•.••..........••••.........•.••..•.....•...............•......................•... LB-42
LM358 .•............•............••.••....••••••.••.... AN-116, AN-247, AN-271, AN-274, AN-284, AN-298, Appendix C
LM358A ...............•..............................................................................•Appendix 0
LM359 •.......•..•........•..•.........••.•.........••..................•...................•...... AN-278,AB-24
LM360 .•••.•.....•....•............•.•••............••.......•...•.••..............•.................•.....AN-87
LM361 •.....•.•••••••..•.•••...•......•••••••.•......••.••....•.....•.••.••...........•.•••.•...•.. AN-87,AN-294
LM363 .••.....•.....................•••...•........••••..........•...•...........•..•.......•......•.•....AN-27l
LM380 •...•••••.•••....•••....•........•.•..........•........•........................•..••.•..•... AN-69, AN-146
LM381 ••.....••.•••.....••.•••••......••••..............•....•.........••.............••••..•..•... AN-64,AN-l04
LM382 .••.........................•.•••...•....•.••••••.........••.••............•..•.......•..•....••....AN-147
LM385 •.......•••.•.•.• , .•••••••.•.....•.•••.....•....••••• AN-242, AN-256, AN-30l, AN-344, AN-460, AN-693, AN-777
LM386 .••............•.............•••............•.••..............................••.......•......•...... LB-54
LM389 .....•••••......••.••...........••••............•••••...........••.••....... AN-256, AN-263, AN-264, AN-274
LM391 ...•.....•..•••••....•.•.••••••••...•.••••••••..•...•••••••••.••.........•..••.•....•......•••••.... AN-272
LM392 .•.••..•..•..................................•...........................................•..AN-274, AN-286
LM393 ........•••.•••.....•••••••.•..•••••••••••..••..•••••••.••.•...•.•.•••••..•. AN-271, AN-274, AN-293, AN-694
LM394 •••••.....•.....•...•...........•............• AN-262, AN-263, AN-264, AN-271, AN-293, AN-299, AN-3ll, LB-52
LM395 .•.......•••••••.....•.••••••.••.•.•.•••••.••. AN-178, AN-l 81, AN-262, AN-263, AN-266, AN-30l, AN-460, LB-28
LM399 .••••.••..•........................••..........•.•.........•....••.•.............•.•...•.....•..••.•AN-l 84
LM555 .••••.•••.......••••••.•........•••..•..........•••.•..•........•••••.•.........••.•.••••.•... AN-694,AB-7
LM556 •.......••••••••••...•.••.••••••..••...••••.••••.........•••.••.........•....••.......•....••.••.....• AB-7
LM565 .•.••••..........••.•.•.........••••..••......•..••••...........•.••••..........••••••....•.. AN-46, AN-146
LM566 •...•...•••.•••••...•....••.•••••.•.....••••.•••............••••.................•..........••.•.... AN-146
LM604 .•••.•••••....•..••.••..•....•....••••....•.....••••.••..........••••••...••.....••••••••..•....•.•• AN-460
LM628 •..•.••••.••.....•.••••••.••....•.••••••.•••.••...•.•••••..•..•.......••••..•••.....•..••••• AN-693,AN-706
LM629 .....•.........•• , .•..........••....•..............•............................••.. AN-693, AN-694, AN-706
LM709 ., ••.••.....•....•.•..•..•.......•••••••.•.•..•••.•.•.•.•.••.....•.•••.•.•••••..•....••••.•••• AN-24, AN-30
LM710 ...........•.•••..........•.•••............•...•....................................•.....•...AN-41, LB-12
LM725 .•••..••...••....••.•............•••••.•...••..•.••.••••.•.•...•.•.••..•.•••.•.•.....•••.•.•.••....•• LB-22
LM741 ..........................................•.................•..........•.........AN-75,AN-79, LB-19, LB-22
LM832 •..•.•.....•...••.........•.•.•••............•...............•...................•.•......•.AN-386, AN-390
LM833 .••••••.••.........•••.•..........•.•.•.•.•......•••.•••••.•.•.....•.••••.•••••...•....••••..••....• AN-346
LM1036 ...........••.•.....•..............•..........•...•........•....•..............•.•...............•.AN-390
LM1310 ••••..•......•..•••.....•......••••..•..•.......•.••••••...•......•••••••.•••••..••••.••••..•....... AN-81
LM1458 ..........••••••.......•.•••. , ••........•......•.•........................•........................ AN-116
LM1524 .........•...••.....•..............•......•......•..............•.......... AN-272, AN-288, AN-292, AN-293
LM1558 •••..•...........•••••........••••••••.•.••••.........•••••••.•.......•.•...••...•....•..•••••....• AN-116
LM1578A ......•..•••••.......•....•.•........•...............................•.....•................••....AB-30
LM1807 ...............................................................................................AppendixB

8-8

DevicelApplication Literature Cross-Reference (Continued)
Device Number

Application Literature

LM1808 ..•.............•..•.•........••..••....•..•..............................•.........•..........AppendixB
LM1820 .•...•......•.•....•.................••..•..•••••..•...•••..••..•••••••.•••.•••.•.••.••••.••.••••••. LB-29
LM1828 ..•.............••...••.••.•........•.......•.............•........•....•...•...•............•.AppendixB
LM1830 ..........•.........•.............••...•.....•............•..............................•..........AB-10
LM1845 ........••..•...•..............•....•....•.•......•..••.•.••....••••••.•••..•...••...•...•••.••AppendixB
LM1865 ...........................................................................................AN-382, AN-390
LM1894 ............•............................•.....•............•••...•..•••..••.••••..AN-384, AN-386, AN-390
LM2577 ..................••.......•.................•.............................................AN-776,AN-777
LM2878 ....................••.....•...•...••....•...........•......•......•...............................AN-147
LM2907 ....•............•...•.....•.........•........••.••..•.••..•••..•....••.••..•••...•...•.•..•....••. AN-162
LM2917 ................•..•..•........•...•.....••...........••................•..........................AN-162
LM2931 .•............•...............•......•...•.....•..••.•.••.•.••....••..•...•••.•..•.•••••..•••...••.. AB-12
LM2931CT .................................................................................................AB-11
LM3045 ............................••.....•.••....•...••....••..••...•...••.......••...••..•....•..••.....AN-286
LM3046 ..............•...•..•..•........•....•..••....•...••......••....•••.•....•..•....•....•... AN-146, AN-299
LM3064 ........•....•......••....•........••...•....•..•...............•..............................AppendixB
LM3065 .....•.................•......................••..••...••.•..•...••.......•...•...•....•....•..AppendixB
LM3070 ...........................•...•....•...•......•..•••...•.•••.•...............•................Appendix B
LM3071 ...•.........•..............••.•.••.•••..•••...•....•....•..•...•...•••...•..••••.•••.•••..•...Appendix B
LM3089 .........•.............•.....•.•.............•......•..•••.•...••..•••..••..••...••..••...•...•....AN-147
LM3524 ..•............•...•....•....••....•..•••..••..•••........•...........•....AN-272, AN-288, AN-292, AN-293
LM3525A ...••..................................•....•...•....•...•...••..•••..••.••.••.•...••...••....•.. AN-694
LM3578A .................•.•.•.••...•••...••.••........•.....•..•........•...•............•..•.....•......AB-30
LM3900 .•...•..........•.........•..............•...•........••....... AN-72, AN-263, AN-274, AN-278, LB-20, AB-24
LM3909 ....••..•.•...•....•.•.•...•........••..•••.......... _...•......................................... AN-154
LM3911 ..........•....••..••..•.••.••...••.••••.•••...••..••...••.••••...•........•..••..•••.•••... LB-27, AN-460
LM3914 .....••..•....•..........•.................•.•........•........•....•...•...•...•.....AN-460, LB-48, AB-25
LM3915 .........•..............•.•..••..••..••••••••.•••••.•.•••••.••..•••...••..••.•••..•••.••.•••••••.•• AN-386
LM3999 ....•....•....••...•.•.•.................•...•...•...••............•............•......•....•.....•AN-161
LM4250 .•....•...••....••.••...•...•••..•••.••••••••.••••••••.••••.•••..•••.•...•••••.•.•••..•••.... AN-88, LB-34
LM7800 ..•.•...•..•...••........••.••...••..•••.••••.•.•.•.•••••••.•••.••••••••••••.••••••..•••.•••••...•. AN-178
LM78L12 ...•..••••..•...••..••........•..••....•..••...•..•.•...•......................•...........•....•AN-146
LM78S40 ..........................•....•...••...•••.••..••..•••..•••.•••..•...••••••••..•..•••..••...•.•. AN-711
LMC555 ...•...•••..•..••••.•••..••.•..•.•.•.•.••.••••.••..•.•••••...•.••.•...•...•...•••..•...•....•.....AN-460
LMC835 ................•......••...••..•...••...•••.•••.••...••..••••.••..•.••••.•.••..••..•••.•••••.•.••AN-435
LMD18200 ..••...........•........................•..........•..•..............•...•.............•...••...AN-694
LM18293 .........•....•...•...•....•...••..••••.••...•••••...•••.•.••.•••.•••••••••.••..•••..•.•..•••..•. AN-706
LP324 ..•................••.......•..........•..........•....••..•....•..••...•...........•..............•AN-284
LP395 •...•...•....••..••..••..•.•..••.••••••••••.••.••••.••.••••••.••.•••.••••.•••.••••.••••.•••••••..••. AN-460

8-9

DevlcelApplication Literature Cross-Reference (Continued)
Device Number

Application Literature

MF10 ••••••.••••••••••••••••••••••••.•••.••..••.••••••••••••••••.•••••.•••••.••••••••••.•••.••••..••••••.• AN-307
MM2716 ••.•••..•.••••••••.••••.•••••.•.•••••••.•.••.••••••.••••••••.••.••.•••••..••••••.••.••.•••.•..•••.• LB-54
MM54104 ••••••••.••••••.•.•.•.••••••••••.•••.••••••.••••.••••.•.•.•••••••.•••••••••..•••.•. AN-252, AN-287, LB-54
MM57110 .• , •.• , •••••••••.••••.•••.•. " •••..••••••••••••••.•••• , .••••••••••..•.•.•. " ., .• , ••. " ••.••• " ., .AN-382
MM74COO •••••••.••.•.•••.••••••.•••••• " •.••••••••••.•.•••..••••.•••.•.•••.••••.•.••••.••••.••.•••••••.•.• AN-88
MM74C02 •.••••.••••••••••.•••••••••••••••.•••••••.••.••••••.••••••••••••••.••.•••.••••.••••.••••.•••••...• AN-88
MM74C04 •••••••••••..•••••••••.•.•••.•••••••••••.••••.••••.•••••.•••••.•••.•.•.•.•••..•.•••••••••••••••••• AN-88
MM74C948 .••••••••.•••••••.•.••••••.•••••••••••••••••••••••••.••••.•••.•.•••••••••••.••••.•••..•••••••.•• AN-193
MM74LS138 ................................................................................................ LB-54
MM53200 .•••.••••••••••••.••.••.•••••.•..•••.•.••••••••••••••.•••••••••.•.••••••••••••••.••••.•••.••••••• AN-290
2N4339 •.•••••••••••••••••••••••••••.•••••.••••..•••••••••.•••••.•••••••••••••••.•.••...••.•••..•••••.•.••• AN-32

8-10

~National

~ Semiconductor

o

Appendix C
Summary of Commercial Reliability Programs

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9.
General

Typical A + Flow is:

National Semiconductor Commercial Reliability Programs
provide a broad range of off-the-shelf enhanced semiconductor products that supply an extra measure of quality and
reliability needed in high-stress or difficult to service applications.
National's A + and B + programs allow each individual customer to:

•
•
•
•

SEM
Assembly and Seal
Four Hour 150'C Bake
Five Temperature Cycles (O'C to + 100'C)

• High Temperature Electrical Test
• Electrical Test
• Burn-In (160 hours at a minimum junction temperature of
125'C)

• Minimize the need for incoming electrical inspection
• Eliminate the need and associated costs of using independent testing laboratories

• DC Parametric and Function Tests
• Tightened Quality Control Inspection Plans

• Reduction in infant mortality rate
• Reduction in reworked board costs
• Reduction in warranty and service costs

Note: Certain products may follow slightly different process flows dictated
by specific capabilities and device characteristics, consult NSC.

P + Product Enhancement

A + Product Enhancement

The P+ product enhancement program applies to power
devices and offers an added advantage. P + involves dynamic tests that screen out assembly related and silicon
defects that can lead to infant mortality andlor reduce the
survivability of the device under high stress conditions. This
includes but is not limited to the following devices:

The A + Product Enhancement incorporates the benefits of
the Multiple-Pass and Elevated Temperature along with
"BURN-lN."
The A + Program provides:
• 100% Temperature Cycling
• 100% Electrical Testing at Room and High Temperature
• 100% Burn-In Testing Combining Increased Temperature with Applied Voltage
• Acceptable Quality Levels Greater than Industry Norm

8-11

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Package Types
Device

a.

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TO-3
KSTEEL

TO-39
(H)

T0-220
(T)

T0-202
(P)

X

X

X

X

LM12

X

LM109/309

X

X

~

LM117/317

X

X

LM117HVl317HV

X

X

·2

LM120/320

X

X

~

LM123/323

X

LM133/333

X

8

LM137/337

X

X

'0

LM137HV/337HV

X

X

~

LM138/338

X

X

E
E

LM140/340

X

X

LM145/345

X

U)

LM150/350

X

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LM195/395

X

LM196/396

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X

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X

X
X

X

X
X

X

LM2930/2935/2984

X

LM2937

X

LM2940/2941

X

LM2990/2991

X

LM2575/2575HV

X

LM2576

X

LM2577
LMD18200/18201

X
X

LM18298

X

8-12

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.--------------------------------------------------------------------.>
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Appendix D
Military Aerospace Programs
from National Semiconductor
This appendix is intended to provide a brief overview of
military products available from National Semiconductor. For further information, refer to our 1987 Reliability
Handbook.

Process Flows
(Integrated Circuits)
JANS

National Semiconductor's Military/Aerospace Program is
founded on dedication to excellence. National offers com·
plete support across the broadest range of products with
the widest selection of qualification levels and screening
flows. These flows include:

JANB

SMD

8-13

iif

~

~

~

1
Description

-a

a

CD

QPL products processed to
MIL-M-38510 Level S for space
level applications.
QPL products processed to
MIL-M-38510 Level B for military
applications.
Standard Military Drawing products
processed to Level B with Table I
Electricals controlled by DESC.
(Formally called DESC Drawing.)

883

Products processed to
MIL-STD-883 Level B for military
applications.

MLP

Products processed on the
Monitored Line (Program)
developed by the Air Force for
space level applications.

MILS

Non-JAN products processed to
Level S to negotiated electrical
specifications for space level
applications.

-MIL

Similar to MIL-STD-883 with
exceptions noted on Certificate of
Conformance.

MSP

Military Screening Program for
initial release of advanced
products.

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• MIL·M·38510: The MIL-M-38510 Program, which is

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sometimes called the JAN IC Program, is administered
by the Defense Electronics Supply Center (DESC). The
purpose 01 this program is to provide the military community with standardized products that have been manufactured and screened to government-controlled specifications in government certified facilities. All 3851 0
manufacturers must be formally qualified and their products listed on DESC's Qualified Products List (QPL) before devices can be marked and shipped as JAN product.
There are two processing levels specified within MIL-M38510: Class Sand B. Class S is typically specified for
space flight applications, while Class B is used for aircraft, naval and ground systems. National is a major
supplier of both classes of devices. Screening requirements are outlined in Table III.
Tables I and" explain the JAN device marking system.
Copies of MIL-M-38510, the QPL and other related
documents may be obtained from:
Naval Publications and Forms Center
5801 Tabor Avenue
Philadelphia, PA 19120
(212) 697-2179
• Standard Military Drawings (SMD): SMD's are issued
to provide standardized versions of devices which are
not available as JAN product. MIL-STD-883 Class B
screening is coupled with tightly controlled electrical
specifications which have been written to allow a manufacturer to use his standard electrical tests. A current
listing of National's SMD offerings can be obtained
from our authorized distributors, sales offices or DESC.
DESC is located in Dayton, Ohio.
• MIL-5TD·883: Although originally intended to establish
uniform test methods and procedures, MIL-STD-883
has also become the general specification for non-JAN
military product. Revision D of this document defines
the minimum requirements for a device to be marked
and advertised as 883-compliant. Included are design
and construction criteria, documentation controls, electrical and mechanical screening requirements, and quality control procedures. Details can be found in paragraph 1.2.1 of MIL-STD-883.

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National offers both 883 Class Band 883 Class S product. The screening requirements for both classes of product are outlined in Table III.
As with SMDs a manufacturer is allowed to use his standard electrical tests provided that all critical parameters
are tested. Also, the electrical test parameters, test conditions, test limits and test temperatures must be clearly
documented. At National Semiconductor, this information
is available via our Table I (formerly RETS, Reliability
Electrical Test Specification Program). The Table I document is a complete description of the electrical tests performed and is controlled by our QA department. Individual
copies are available upon request.
Some of National's products are produced on a flow similar to MIL-STD-883. These devices are screened to the
same stringent requirements as 883 product, but are
marked as ·MIL; specific reasons for prevention of compliancy are clearly defined in the Certificate of Conformance (C of C) shipped with the product.
• Monitored Line Program (MLP): is a non JAN Level S
program developed by the Air Force. Monitored Line
product usually provides the shortest cycle time, and is
acceptable for application in several space level programs. Lockheed Missiles and Space Company in ~un­
nyvale, Califomia, under an Air Force contract, provides
"on-site" monitoring of product processing, and as appropriate, program management. Monitored Line orders
generally do not allow "customizing", and most flows
do not Include quality conformance inspection. Drawing
control is maintained by the Lockheed Company.
• Military Screening Program (MSP): National's Military
Screening Program was developed to make screened
versions of advanced products such as gate arrays and
microprocessors available more quickly than is possible
for JAN and 883 devices. Through this program,
screened product is made available for prototypes and
breadboards prior to or during the JAN or 883 qualification activities. MSP products receive the 100% screening of Table III, but are not subjected to Group C and D
quality conformance testing. Other criteria such as electrical testing and temperature range will vary depending
upon individual device status and capability.

8-14

TABLE I. The MIL-M-38510 Part Marking

TABLE II. JAN Package Codes

~~82!E/X~~XYYY

38510
Package
Designation

[~n~.
A= Solder Dipped

B=TIn Plate
C= Gold Plate
X= Any lead finish above
Is acceptable
Device Package
(see Table II)
- Screening Level
S, B, or C
'---- Device Number on
Slash Sheet
' - - - Slash Sheet Number
For radiation hard devices
this slash Is replaced by the
Radiation Hardness Assurance
Designator ~Iot, D, R, or H per
paragraph .4.1.3 of IIIL-Iot38510)
IIIL-II-38S10
JAN Prefix
(which may b. applied only to
a fully conformant device par
taraaraphs 3.6.2.1 and 3.6.7 of
IL- -38510)
TL/XX/OO30-1

A
B
C

0
E
F
G

H
I

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K
L
M
N
P

a
R
S
T
U

V
W

X

y
Z

2
3

Microcircuit Industry Description
14-pin %" x %" (Metal) Flatpak
14-pin 0/.." x %" (Metal) Flatpak
14-pin %" x %" Dual-In-Line
14-pin %" x %" (Ceramic) Flatpak
16-pin %" x 7,Ia" Dual-In-Line
16-pin %" x %" (Metal or Ceramic) Flatpak
a-pin TO-99 Can or Header
10-pin %" x %" (Metal) Flatpak
10-pin TO-100 Can or Header
24-pin 1f2" x 1%" Dual-ln·Line
24-pin %" x %" Flatpak
24-pin %" x 1%" Dual-ln·Line
12-pln TO-101 Can or Header
(Note 1)
a-pin %" x %" Dual-In-Line
40-pin 0/.8" x 2Yt8" Dual-In-Line
20-pln %" x 1Yt8" Dual-ln-L1ne
20-pin %" x 1f2" Flatpak
(Note 1)
(Note 1)
1a-pin %" x 16fte" Dual-ln-L1ne
22-pln %" x 1Ye" Dual-ln-L1ne
(Note 1)
(Note 1)
(Note 1)
20-termlnal 0.350" x 0.350" Chip Carrier
2B-termlnal 0.450" x 0.450" Chip Carrier

Nole 1: Theee letters are aSSigned to packages by Individual MIL-M-38510
detail speclflcaHons and may be assigned to different packages In different
specifications.
TABLE III. 100% Screening Requirements

Method
1.

ClaasB

ClassS

Scrssn

Reqmt

Method

Reqmt

Wafer Lot Acceptance

5007

All Lots

2.

Nondestructive Bond Pull (Note 14)

2023

100%

3.

Internal Visual (Note 1)

2020, Condition A

100%

2010, Condition B

100%

4.

Stabilization Bake (Note 16)

100B, Condition C, Min
24 Hrs. Min

100%

100B, Condition C, Min
24 Hrs. Min

100%

5.

Temperature Cycling (Note 2)

1010, Condition C

100%

1010, Condition C

100%

6.

Constant Acceleration

2001, Condition E Min
y 1 Orientation Only

100%

2001, Condition E Min
Y1 Orientation Only

100%

7.

Visual Inspection (Note 3)

100%

a.

Particle Impact Noise Detection (PIND)

2010, Condition A (Note 4)

100%

9.

Serialization

(Note 5)

100%

Interim (Pre·Burn-ln) Electrical Parameters

Per Applicable Device
Specification (Note 13)

100%

10.

a-15

100%

Per Applicable Device
Specification (Note 6)

TABLE 111.100% Screening Requirements (Continued)
Cla88S

Screen

Method
11.

Burn-In Test

Cla88B
Reqmt

1015
240 Hrs. @ 125°C Min
(Cond. F Not Allowed)

100%

12.

Interim (Post Burn-In)
Electrical Parameters

Per Applicable Device
Specification (Note 3)

100%

13.

Reverse Bias Burn-In (Note 7)

1015; Test Condition A, C,
72 Hrs. @ 150°C Min
(Cond. F Not Allowed)

100%

14.

Interim (Post-Burn-In) Electrical
Parameters

Per Applicable Device
Specification (Note 13)

100%

15.

PDA Calculation

5% Parametric (Note 14),
3% Functional

16.

Final Electrical Test (Note 15)
a) Static Tests
1) 25°C (Subgroup 1, Table I, 5005)
2) Max & Min Rated Operating Temp.
(Subgroups 2, 3, Table I, 5005)
b) Dynamic Tests or Functional Tests
1) 25°C (Subgroup 4 or 7)
2) Max and Min Rated Operating Temp.
(Subgroups 5 and 6 or 8, Table I,
5005)
c) Switching Tests 25°C
(Subgroup 9, Table I, 5005)

Per Applicable Device
Specification

Seal Fine, Gross

1014

18.

Radiographic (Note 10)

2012 Two Views

100%

19.

Qualification or Quality Conformance
Inspection Test Sample Selection

(Note 11)

Samp.

20.

External Visual (Note 12)

2009

100%

17.

All Lots

Method
1015
160 Hrs.

Reqmt
100%

@

125°C Min

Per Applicable Device
Specification
5% Parametric (Note 14)

100%
All Lots

Per Applicable Device
Specification
100%
100%

100%
100%

100%
100%

100%
100%

100%

100%

100%
(Note 8)

1014

(Note 11)

100%
(Note 9)

Samp.
100%

Note 1: Unless otherwise specified, at the manufacturer's option. test samples for Group e, bond strength (Method 5005) may be randomly selected prior to or
following Internal visual (Method 5004), prior to sealing provided all other specification requirernsnts are satisfied (e.g., bond strength requirements shall apply to
each inspection lot, bond failures shall be counted even Hthe bond would have failed Internal vlsuaO.
Note 2: For Class e devices, this test may be replaced with thermal shock Method 1011, Test Condition A, minimum.
Note 3: At the manufacturer's option, visual inspection for calestrophic failures may be conducted after each of the thermal/mechanical screens, altar the
sequence or after seal test Catestrophlc failures are defined as missing leads, broken packages, or lids off.
Note 4: The PIND test may be performed in any sequence altar step 6 and prior to step 16. See MIL·M·38510, paragraph 4.6.3.
Note 5: Class S devices shall be serialized prior to interim electrical parameter measurements.
Note 6: When spacified, all devices shall be tested for those parameters requiring delta calculations.
Note 7: Reverse bias burn-in Is a requirement only when specified in the eppHcsble device specHication. The order of performing bum-in and reverse bias bum·in
may be inverted.
Note 8: For Class S devices, the seal test may be performed In any sequence between step 16 and step 19, but it shall be performed altar all shesring and forming
operations on the terminals.

Note 9: For Class e devices, the fine and gross seal lasts shall be performed separately or together In any sequence and order between step 6 and step 20 except
that they shall be performed after all shearing and forming operations on the terminals. When 100% seal screen cannot be performed after shearing and forming
(e.g., flstpaka and chip carrlera) the seal screen shall be done 100% prior to these operations and a sample test (LTPD = 5) shall be performed on each inspection
lot following these operations. If the sample falls, 100% rescreening shall be required.
Note 10: The radiographic screen may be performed in any sequence after step 9.
Note 11: Samples shall be selected for testing In accordance with tha specifiC device class and lot raquirernsnts of Method 5005.
Note 12: External Visual shall be performed on the lot any time after step 19 and prior to shipment.
Note 13: Read and record is required at steps 10 and 12 only for those parameters for which post-burn~n delta msaaurements are speclfled. All parameters shall
be read and reoorded at step 14.
Note 14: The PDA shall apply to all subgroup 1 parameters at 25"C and all delta parameters.
Note 15: Only one view is required for flat paCkages and lesdless chip carriers with leads on all four sides.
Note 16: May be performed at any tirns prior to step 10.

8-16

Military Analog Products Available from National Semiconductor

Device

Package
Styles
(Note 1)

Description

Process
Flows
(Note 2)

SMD/JAN
(Note 3)

HIGH PERFORMANCE AMPLIFIERS AND BUFFERS
LF147
LF155
LF155A
LF156
LF156A
LF157
LF157A
LF411M
LF412M
LF441M
LF442M
LF444M

D,J
J,W,H
H
J,W,H
H
H
H
H,J
H,J
H
H
D

Wide BW Quad JFET Op Amp
JFET Input Op Amp
JFET Input Op Amp
JFET Input Op Amp
JFET Input Op Amp
JFET Input Op Amp
JFET Input Op Amp
Low Offset, Low Drift JFET Input
Low Offset, Low Drift JFET Input-Dual
Low Power JFET Input
Low Power JFET Input-Dual
Low Power JFET Input-Quad

SMD/JAN
BB3/JAN
BB3
BB3/JAN
BB3
BB3
BB3
BB3/JAN
BB3/JAN
B83
883
883

LHOO02
LH0021
LH0024
LH0032
LH0041
LH0061
LH0101
LH4118
LH4161
LH4162

H
K
H
G
G
K
K
G
H
H

Buffer Amp
1.0 Amp Power Op Amp
High Slew Rate Op Amp
Ultra Fast FET-Input Op Amp
0.2 Amp Power Op Amp
0.5 Amp Wide Bandwidth Op Amp
Power Op Amp
Low Gain Wide Band RF Amp
Trimmed LM6161 VIP Amp
Dual LH4161

BB3/MIL
8B3/SMD
"-MIL"
BB3/SMD
BB3/SMD
"-MIL"
BB3/SMD

LM10
LM101A
LM108A
LM118
LM124
LM124A
LM146
LMl48
LM158A
LM15B
LM604AM
LM611AM
LM613AM
LM614AM
LM709A
LM741
LM747

H
J,H,W
J,H,W
J,H,W
J,E,W
J,W
J
J,E,W
J, H
J,H
J
J
J,E
J
H,J,W
J,H,W
J,H,W

LM611B
LM6121
LM6125
LM6161
LM6164
LM6165
LM6162

J,E
H
H
J,E,W
J,E,W
J,E,W
J,E,W

VIP Dual Op Amp
VIP Buffer
VI P Buffer with Error Flag
VIP Op Amp (Unity Gain)
VIP Op Amp (Av > 5)
VIP Op Amp (AV > 25)
VIP Op Amp (AV > 2, - 1)

8B3/SMD
883/SMD
BB3/SMD
BB3/SMD
BB3/SMD
883/SMD
883/SMD

5962-91565
5962-90812
5962-90815
5962-B9621
5962-B9624
5962-B9625
5962-92165

LMC660AM
LMC662AM
LPC660AM
LPC662AM

J
J
J
J

Low Power CMOS Quad Op Amp
Low Power CMOS Dual Op Amp
Micropower CMOS Quad Op Amp
Micropower CMOS Dual Op Amp

883/SMD
883/SMD
883/SMD
883/SMD

TBD
TBD
TBD
TBD

OP07

H

Precision Op Amp

SMD/JAN

113502

Super-Block™ Micropower Op Amp/Ref
General Purpose Op Amp
Precision Op Amp
FastOpAmp
Low Power Quad Op Amp
Low Power Quad
Quad Programmable Op Amp
. Quad 741 Op amp
Low Power Dual Op Amp
Low Power Dual Op Amp
Super-Block 4 Channel Mux Amp
Super-Block Op Amp/Reference
Super-Block Dual Op Amp/Dual Comp/Ref
Super-Block Quad Op Amp/Ref
General Purpose Op Amp
General Purpose Op Amp
General Purpose Dual Op Amp

8-17

"_MIL"
"-MIL"
"-MIL"
883/SMD
883/JAN
B83/JAN
B83/JAN
BB3/JAN
883/JAN
B83
BB3/JAN
883/SMD
BB3/SMD
8B3/SMD
883/SMD
8B3/SMD
BB3/SMD
883/SMD
8B3/JAN
883/JAN

/11906
/11401

/11402
-

-

/11904
/11905

7801301
B5088

BOO13
B50B7

850B9

-

5962-87604
/10103
/10104
/10107
/11005
/11006

/11001
5962-B771 002
5962-B771 001
5962-B9639
TBD
TBD
TBD
7B00701
110101
110102

•

Military Analog Products Available from National Semiconductor (Continued)
Device

Package
Styles
(Note 1)

Description

Process
Flows
(Note 2)

SMD/JAN.
(Note 3)

COMPARATORS
LF111
LH2111
LM106
LM111
LM119
LM139
LM139A
LM160
LM161
LM193A
LM612AM
LM613AM

H
J,W
H,W
J,H,E,W
J,H,E,W
J,E,W
J
J,H
J, H
J, H
J
J, E

LM615AM
LM710A'
LM711A'
LM760

J
J,H,W
J,H,W
J,H

Voltage Comparator
Dual Voltage Comparator
Voltage Comparator
Voltage Comparator
High Speed Dual Comparator
Quad Comparator
Precision Quad Comparator
High Speed Differential Comparator
High Speed Differential Comparator
Dual Comparator
Dual-Channel Comparator/Reference
Super-Block Dual Comparator/
Dual Op Amp/ Adj Reference
Quad Comparator/Adjustable Reference
Voltage Comparator
DualLM710
High Speed Differential Comparator

"-MIL"
883/JAN
883/SMD
883/JAN
883/JAN
883/JAN
883/SMD
883/SMD
883/SMD
883/JAN
883/SMD
883/SMD

-

883/SMD
883/JAN
883/JAN
883/JAN

TBD
/10301
/10302
5962-87545

/10305
8003701
/10304
/10306
/11201
5962-87739
8767401
5962-87572
/11202
TBD
TBD

'Formerly manufactured by Fairchild Semiconductor as parl numbers jlA710 and jlA711.

LINEAR REGULATORS
Positive Voltage Regulators
LH0075
G
LM105
H
LM109
H
LM109
K
LM117
H,E,K
LM117A
H
LM117A
K
LM117HV
H
LM117HV
K
LM123
K
LM138
K
LM140H-5.0
H
LM140H-8.0
H
LM140H-8.0
H
LM140H-12
H
LM140H-15
H
LM140H-24
H
LM140AK-5.0
K
LM140AK-12
K
LM140AK-15
K
LM140K-5.0
K
LM140K-12
K
LM140K-15
K
LM140K-24
K
LM140LAH-5.0
H
LM140LAH-12
H
LM140LAH-15
H
LM150
K
LM2940K-5.0
K
LM2940K-8.0
K
LM2940K-12
K
LM2940K-15
K
LM2941K
K
LM723
H,J,E
LM78MG
H
LP2951
H,E,J
LP2963AM
J

Precision Voltage Regulator
Adjustable Voltage Regulator
5V Regulator, 10 = 20 mA
5V Regulator, 10 = 1A
Adjustable Regulator
Precision Adjustable Regulator, 10 = 0.5A
PreCision Adjustable Regulator, 10 = 1,5A
Adjustable Regulator, 10 = 0.5A
Adjustable Regulator, 10 = 1.5A
3A Voltage Regulator
5A Adjustable Regulator
0.5A Fixed 5V Regulator
0.5A Fixed 8V Regulator
0.5A Fixed 8V Regulator
0.5A Fixed 12V Regulator
0.5A Fixed 15V Regulator
0.5A Fixed 24V Regulator
1.0A Fixed 5V Regulator
1.0A Fixed 12V Regulator
1.OA Fixed 15V Regulator
1.0A Fixed 5V Regulator
1.0A Fixed 12V Regulator
1.0A Fixed 15V Regulator
1.2A Fixed 24V Regulator
100 mA Fixed 5V Regulator
100 mA Fixed 12V Regulator
100 mA Fixed 15V Regulator
3A Adjustable Power Regulator
5V Low Dropout Regulator
8V Low Dropout Regulator
12V Low Dropout Regulator
15V Low Dropout Regulator
Adjustable Low Dropout Regulator
Precision Adjustable Regulator
Adjustable Regulator
Adjustable Mlcropower LDO
250 mA Adj. Mlcropower LDO

8-18

"-MIL"
883/SMD
883/JAN
883/JAN
883/JAN
883/SMD
883/SMD
883/SMD
883/SMD
883
"-MIL"
883/JAN
883
883
883/JAN
883/JAN
883
883
883
883
883/JAN
883/JAN
883/JAN
883/JAN
883
883
883
883
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883/JAN
883
883/SMD
883

-5962-89588
/10701BXA
/10701BYA
/11703,111704

7703405XA
7703405YA
7703402XA
7703402YA

--

/10702

-

/10703
/10704

---/10706
/10707
/10708
/10709

-

-5962-89587
5962-90883
5962-90884
5962-90885
TBD
/10201

-5982-38705
-

Military Analog Products Available from National Semiconductor (Continued)

Device

Package
Styles
(Note 1)

Description

Process
Flows
(Note 2)

SMD/JAN
(Note 3)

LINEAR REGULATORS (Continued)
Negative Voltage Regulators
LH0076

G

Precision Programmable Regulator

"-MIL"

-

LM104

H

Precision Negative Regulator

883/SMD

5962-87605

LM120H-5.0
LM120H-8.0
LM120H-12
LM120H-15

H
H
H
H

Fixed 0.5A Regulator, VOUT
Fixed 0.5A Regulator, VOUT
Fixed 0.5A Regulator, VOUT
Fixed 0.5A Regulator, VOUT

883/JAN
883
883/JAN
883/JAN

LM120K-5.0
LM120K-12
LM120K-15

K
K
K

= -5V
= -8V
= -12V
= -15V
Fixed 1.0A Regulator, VOUT = -5V
Fixed 1.0A Regulator, VOUT = -12V
Fixed 1.0A Regulator, VOUT = -15V

883/JAN
883/JAN
883/JAN

/11505
/11506
/11507

LM137A
LM137A
LM137
LM137HV
LM137HV

H
K
H,K
H
K

Precision Adjustable Regulator
Precision Adjustable Regulator
Adjustable Regulator
Adjustable (High Voltage) Regulator
Adjustable (High Voltage) Regulator

883/SMD
883/SMD
883/JAN
883/SMD
883/SMD

7703406XA
7703406YA
/11803,/11804
7703404XA
7703404YA

LM145K-5.0
LM145K-5.2

K
K

Negative 3 Amp Regulator
Negative 3 Amp Regulator

883/SMD
883

LM79MG

H

Adjustable Regulator

883

-

K
K
K
K
K
K
K
K
K
K
K

Simple Switcher™ Step-Down, VOUT = 5V
Simple Switcher Step-Down, VOUT = 12V
Simple Switcher Step-Down, VOUT = 15V
Simple Switcher Step-Down, Adj VOUT
Simple Switcher Step-Down, VOUT = 5V
Simple Switcher Step-Down, VOUT = 12V
Simple Switcher Step-Down, VOUT = 15V
Simple Switcher Step-Down, Adj VOUT
Simple Switcher Step-Up, VOUT = 12V
Simple Switcher Step-Up, VOUT = 15V
Simple Switcher Step-Up, Adj VOUT

883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD

TBD
TBD
TBD
TBD
TBD
TBD
TBD
TBD
TBD
TBD
TBD

LM1578

H

750 mA Switching Regulator

883/SMD

5962-89586

LM78S40'

J

Universal Switching Regulator Subsystem

883/SMD

5962-88761

883/SMD
883/SMD
883/SMD
883/SMD

7702806
7702807
7702808
7702809

/11501

/11502
111503

5962-90645

SWITCHING REGULATORS
LM1575-5
LM1575-12
LM1575-15
LM1575-ADJ
LM1575HV-5
LM1575HV-12
LM1575HV-15
LM1575HV-ADJ
LM1577-12
LM1577-15
LM1577-ADJ

'Forme~y

manufactured by Fairchild Semioonductor as the ,..A7BS40DMQB.

VOLTAGE REFERENCES

= 3.0V
= 3.3V
= 3.6V
= 3.9V

LM103-3.0
LM103-3.3
LM103-3.6
LM103-3.9

H
H
H
H

Reference Diode, BV
Reference Diode, BV
Reference Diode, BV
Reference Diode, BV

LM113
LM113-1
LM113-2

H
H
H

Reference Diode with 5% Tolerance
Reference Diode with 1 % Tolerance
Reference Diode with 2% Tolerance

883/SMD
883/SMD
883/SMD

5962-8671101
5962-8671102
5962-8671103

LM129A
LM129B
LM136A-2.5
LM136A-5.0
LM136-2.5
LM136-5.0

H
H
H
H
H
H

Precision Reference, 10 ppm/oC Drift
Precision Reference, 20 ppml"C Drift
2.5V Reference Diode, 1 % VOUT Tolerance
5V Reference Diode, 1 % VOUT Tolerance
2.5V Reference Diode, 2% VOUT Tolerance
5V Reference Diode, 2% VOUT Tolerance

883/SMD
883/SMD
883
883/SMD
883
883

5962-8992101 XA
5962-8992102XA

8-19

8418001

-

-

Military Analog Products Available from National Semiconductor (Continued)
Package
Styles
(Note 1)

Description

Process
Flows
(Note 2)

H
H,E
H
H
H
H
H,E
H,E
H
H
H
J
J
J,E
J
J
H
H
H

10V Precision Reference, Low Tempco 0.05% Tolerance
Adjustable Micropower Voltage Reference
2.5V Micropower Reference Diode, Ultralow Drift
Adjustable Micropower Voltage Reference
1.2V Micropower Reference Diode, Low Drift
2.5V Micropower Reference Diode, Low Drift
1.2V Micropower Reference Diode, Low Drift
2.5V Micropower Reference Diode, Low Drift
Precision Reference, Low Tempco
Precision Reference, UltralowTempco
Precision Reference, Ultralow Tempco
Super-Block Op Amp/Reference
Super-Block Dual-Channel Comparator/Reference
Super-Block Dual Op Amp/DuaIComp/Dual Ref
Super-Block Quad Op Amp/Reference
Super-Block Quad Comparator/Reference
Precision BCD Buffered Reference
Precision BCD Buffered Reference
Precision BCD Buffered Reference

883/SMD
883
883/SMD
883
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
883
883/SMD
883/SMD
883/SMD
883/SMD
883/SMD
"-MIL"
"-MIL"
II_MIL"

ADC08020L
ADC0851

J
J

883/SMD
883/SMD

5962-90966
TBD

ADC0858

J

883/SMD

TBD

ADC1241CM

J

883/SMD

TBD

ADC12441CM
ADC1251CM

J
J

883/SMD
883/SMD

TBD
TBD

ADC12451CM
ADCl 0061 CM
ADC10062CM

J
J
J

883/SMD
883/SMD
883/SMD

TBD
TBD
TBD

ADC10064CM

J

883/SMD

TBD

ADC08061CM
ADC08062CM

J
J

883/SMD
883/SMD

TBD
TBD

ADC08064CM

J

883/SMD

TBD

ADC08068CM

J

8-Bit ",P-Compatible
8-Bit Analog Data Acquisition
& Monitoring System
8-Bit Analog Data Acquisition
& Monitoring System
12-Bit Plus Sign Self-Calibrating
with Sample/Hold Function
Dynamically-Tested ADC1241
12-Bit Plus Sign Self-Calibrating
with Sample/Hold Function
Dynamically-Tested ADC1251
10-Bit Multistep ADC
10-Bit Multistep ADC w/Dual
Input Multiplexer
10-Bit Multistep ADC w/Quad
Input Multiplexer
8-Bit Multistep ADC
8-Bit Multistep ADC w/Dual
Input Multiplexer
8-Bit Multistep ADC w/Quad
Input Multiplexer
8-Bit Multistep ADC w/Octal
Input Multiplexer

883/SMD

TBD

Device

SMD/JAN
(Note 3)

VOLTAGE REFERENCES (Continued)
LM169
LM185
LMI85BXH2.5
LM185BY
LMI85BYH1.2
LM185BYH2.5
LMI85-1.2
LMI85-2.5
LM199
LM199A
LM199A-20
LM611AM
LM612AM
LM613AM
LM614AM
LM615AM
LH0070-0
LH0070-1
LH0070-2

TBD

5962-8759404
5962-8759405
5962-8759406
5962-8759401
5962-8759402
5962-8856102
5962-8856101

-

TBD
TBD
TBD
TBD
TBD

-

-

DATA ACQUISITION

8-20

Military Analog Products Available from National Semiconductor (Continued)
Package
Styles
(Note 1)

Device

Process
Flows
(Note 2)

SMD/JAN
(Note 3)

6th Order Butterworth Lowpass
6th Order Butterworth Lowpass

883/SMD
883/SMD

5962·90967
5962·90967

4th Order Elliptic Notch
Dual 2nd Order General Purpose

883/SMD
883/SMD

5962·90968
TBt>

Description

DATA ACQUISITION SUPPORT
Switched Capacitor FlltE rs
LMF60CMJ50
LMF60CMJ100
LMF90CM
LMF100A
Sample and Hold
LF198

I

J
J
J
J, E
H

I

Monolithic Sample and Hold

I

SMD/JA

I

5962·87608
/12501

Note 1: 0: Side-Brazed DIP
Nole 2: Process Flows
E: Leadless Ceramic Chip Carrier
JAN = JM38510, Level B
G: Metal Can (TO-8)
SMD = Standard Military Drawing
H: Metal Can (T0-39, TO-5, TO-99, TO-l00)
883 = MIL-STD-883 Rev C
J: Ceramic DIP
-MIL = Exceptions to 883C noted on
K: Metal Can (TO-3)
Certificate of Conformance
W: Flatpak
Note 3: Please call your local sales office to determine price and availability of space-level products. All "LM" prefix products In this guide are avallble with spacelevel processing.

8·21

"

~National

JD
I
f
-u
:e

SemIconducIDr

Appendix E
Understanding Integrated Circuit
Package Power Capabilities

ell

.~

i

f
Q

C

J
c

I

.!!

J

INTRODUCTION
The short and long term reliability of National Semiconductor's interface circuits, like any integrated circuit, is very dependent on its environmental condition. Beyond the mechanical/environmental factors, nothing has a greater influence on this reliability than the electrical and thermal stress
seen by the integrated circuit. Both of these stress issues
are specifically addressed on every interface circuit data
sheet, under the headings of Absolute Maximum Ratings
and Recommended Operating Conditions.
However, through application calls, it has become clear that
electrical stress conditions are generally more understood
than the thermal stress conditions. Understanding' the importance of electrical stress should never be reduced, but
clearly, a higher focus and understanding must be placed on
thermal stress. Thermal stress and its application to interface circuits from National Semiconductor is the subject of
this application note.

Failure rate is the number of devices that will be expected to
fail in a given period of time (such as, per million hours). The
mean time between failure (MTBF) is the average time (in
hours) that will be expected to elapse after a unit has failed
before the next unit failure will occur. These two primary
"units of measure" for device reliability are inversely related:
MTBF=

. I
Failure Rate
Although the "bathtub" curve plots the overall failure rate
versus time, the useful failure rate can be defined as the
percentage of devices that fail per-unit-time during the flat
portion of the curve. This area, called the useful life, extends
between tl and t2 or from the end of infant mortality to the
onset of wearout. The useful life may be as short as several
years but usually extends for decades if adequate design
margins are used in the development of a system.
Many factors influence useful life including: pressure, mechanical stress, thermal cycling, and electrical stress. However, die temperature during the device's useful life plays an
equally important role in triggering the onset of wearout.

FACTORS AFFECTING DEVICE RELIABILITY
Figure 1 shows the well known "bathtub" curve plotting failure rate versus time. Similar to all system hardware (mechanical or electrical) the reliability of interface integrated
circuits conform to this curve. The key issues associated
with this curve are infant mortality, failure rate, and useful
life.

m

EARLY UfE

n

FAILURE RATES vs TIME AND TEMPERATURE
The relationship between integrated circuit failure rates and
time and temperature is a well established fact. The occurrence of these failures is a function which can be represented by the Arrhenius Model. Well validated and predominantly used for accelerated life testing of integrated circuits, the
Arrhenius Model assumes the degradation of a performance
parameter is linear with time and that MTBF is a function of
temperature stress. The temperature dependence is an exponential function that defines the probability of occurrence.
This results in a formula for expreSSing the lifetime or MTBF
at a given temperature stress in relation to another MTBF at
a different temperature. The ratio of Ihese two MTBFs is
called Ihe acceleration factor F and is defined by the following equation:

~

USEfUL UfE

WEAROUT TIME
TLlH/9312-1

FIGURE 1_ Failure Rate va Time
Infant mortality, the high failure rate from time to to tl (early
life), is greatly influenced by system stress conditions other
than temperature, and can vary widely from one application
to another. The main stress factors that contribute to infant
mortality are electrical transients and noise, mechanical
maltreatment and excessive temperatures. Most of these
failures are discovered in device test, burn-in, card assembly and handling, and initial system test and operation. Although important, much literature is available on the subject
of infant mortality in integrated circuits and Is beyond the
scope of this application note.

F = XI = exp
X2

Where: XI =
X2 =
T =
E=

[~(1.
K T2

_1.)]
T1

Failure rate at junction temperature Tl
Failure rate at junction temperature T2
Junction temperature in degrees Kelvin
Thermal activation energy in electron volts
(ev)
K = Boltzman's constant

8-22

However, the dramatic acceleration effect of junction temperature (chip temperature) on failure rate is illustrated in a
plot of the above equation for three different activation energies in Figure 2. This graph clearly demonstrates the importance of the relationship of junction temperature to device failure rate. For example, using the 0.99 ev line, a 30·
rise in junction temperature, say from 130·C to 160·C, results in a 10 to 1 increase in failure rate.

flows from the chip to the ultimate heat sink, the ambient
environment. There are two predominant paths. The first is
from the die to the die attach pad to the surrounding package material to the package lead frame to the printed circuit
board and then to the ambient. The second path is from the
package directly to the ambient air.
Improving the thermal characteristics of any stage in the
flow chart of Figure 4 will result in an improvement in device
thermal characteristics. However, grouping all these characteristics into one equation determining the overall thermal
capability of an integrated circuit/package/environmental
condition is possible. The equation that expresses this relationship is:
TJ = TA + Po (lIJA)
Where: TJ = Die junction temperature
TA = Ambient temperature In the vicinity device
Po = Total power dissipation (In watts)
lIJA = Thermal resistance junction-to-amblent
lIJA' the thermal resistance from device junction-to-ambient
temperature, is measured and specified by the manufacturers of integrated circuits. National Semiconductor utilizes
special vehicles and methods to measure and monitor this
parameter. All circuit data sheets specify the thermal characteristics and capabilities of the packages available for a
given device under speCific conditions-these package
power ratings directly relate to thermal resistance junctlonto-ambient or lIJA.
Although National provides these thermal ratings, it Is critIcal that the end user understand how to use these numbers
to Improve thermal characteristics In the development of his
system using IC components.

~1000k

~

I'! lOOk 1--+---1-+-+.......,-1----1

!!i

1--+---1-+,t~m.H

i

10k

lk

1--+---1--:~~fE_+---1

~

100

t-+--7F-7"IFt--tt-+--i

~

60

90

120 150 180 210

JUNCnoN TEMPERATURE (·C)
TL/H/9312-2

FIGURE 2. Failure Rate as a Function
of Junction Temperature
DEVICE THERMAL CAPABILITIES
There are many factors which affect the thermal capability
of an Integrated circuit. To understand these we need to
understand the predominant paths for heat to transfer out of
the integrated circuit package. This Is illustrated by Figures
Sand 4.
Figure 3 shows a cross-sectional view of an assembled Integrated circuit mounted Into a printed circuit board.
Figure 4 Is a flow chart showing how the heat generated at
the power source, the junctions of the Integrated circuit

DEVICE LEAD

TL/H/9312-3

FIGURE 3. Integrated Circuit Soldered Into a Printed Circuit Board (Cross·Sectlonal View)

DIE
JUNCTION
(ENERGY
SOURCE)

r-+

DIE

....

DIE
ATIACH
PAD

r-+

PACKAGE
MATERIAL

r--.

LEAD
FRAME

-+

PIIINTED
CIRCUIT
BOARD

AIRFILM
AROUND
PACKAGE

-+

AMBIENT

...;...,.

AMBIENT

TL/H/9312-4

FIGURE 4, Thermal Flow (Predominant Paths)

8·23

DETERMINING DEVICE OPERATING
JUNCTION TEMPERATURE
From the above equation the method of determining actual
worst-case device operating junction temperature becomes
straightforward. Given a package thermal characteristic,
9JA, worst-case ambient operating temperature, TA(max),
the only unknown parameter is device power dissipation,
Po. In calculating this parameter, the dissipation of the integrated circuit due to its own supply has to be considered,
the dissipation within the package due to the external load
must also be added. The power associated with the load in
a dynamic (switching) situation must also be considered.
For example, the power associated with an inductor or a
capacitor in a static versus dynamic (say, 1 MHz) condition
is significantly different.
The junction temperature of a device with a total package
power of 600 mW at 70'C in a package with a thermal resistance of 63'C/W is 108'C.
TJ = 70'C + (63'C/W) x (0.6W) = 108'C
The next obvious question is, "how safe is 108'C?"

The slope of the straight line between these two paints is
minus the inversion of the thermal resistance. This Is referred to as the derating factor.
1
Derating Factor = - -9
JA
As mentioned, Rgure 5 is a plot of the safe thermal operating area for a device in a 16-pin molded DIP. As long as the
intersection of a vertical line defining the maximum ambient
temperature (70'C in our previous example) and maximum
device package power (600 mW) remains below the maximum package thermal capability line the junction temperature will remain below 150'C-the limit for a molded package. If the Intersection of ambient temperature and package
power fails on this line, the maximum junction temperature
will be 150'C. Any intersection that occurs above this line
will result in a junction temperature in excess of 150'C and
is not an appropriate operating condition.
2.4

~

MAXIMUM ALLOWABLE JUNCTION TEMPERATURES
What is an acceptable maximum operating junction temperature is in itself somewhat of a difficult question to answer.
Many companies have established their own standards
based on corporate policy. However, the semiconductor in,
dustry has developed some defacto standards based on the
device package type. These have been well accepted as
numbers that relate to reasonable (acceptable) device lifetimes, thus failure rates.
National Semiconductor has adopted these industry-wide
standards. For devices fabricated in a molded package, the
maximum allowable junction temperature is 150'C. For
these devices assembled in ceramic or cavity DIP packages, the maximum allowable junction temperature is
175'C. The numbers are different because of the differences in package types. The thermal strain associated with the
die package interface in a cavity package is much less than
that exhibited in a molded package where the integrated
circuit chip is in direct contact with the package material.
Let us use this new information and our thermal equation to
construct a graph which displays the safe thermal (power)
operating area for a given package type. Figure 5 is an example of such a graph. The end pOints of this graph are
easily determined. For a 16-pin molded package, the maximum allowable temperature is 150'C; at this point no power
dissipation is allowable. The power capability at 25'C is
1.98W as given by the following calculation:
P @25'C
o

iii
"" 1.2

;:;

~

~..rr--iMAXlMUM PACiw;E ( - "'III~ THERMAL CAPABILITY ( - OPERATING~ LINE
AREA

' ' II I'

~

SLOPE=

O.B Po=600ntN
0.4

OPERATING ~

(--

-sk-

....

POINT:*,"---"'I--~,
....
:--t--;
TA= 7O'C'_-t~"""""IE+--1

O~~I--~_-~I~_"'II~~
25 50 75 100 125 150 175
TEMPERATURE ('el
TL/H/9312-5

FIGURE 5. Package Power Capability
vs Temperature
The thermal capabilities of all integrated circuits are expressed as a power capability at 25'C still air environment
with a given derating factor. This Simply states, for every
degree of ambient temperature rise above 25'C, reduce the
package power capability stated by the derating factor
which is expressed in mW I'C. For our example-a 9JA of
63'C/W relates to a derating factor of 15.9 mW I'C.
FACTORS INFLUENCING PACKAGE
THERMAL RESISTANCE
As discussed earlier, improving any portion of the two primary thermal flow paths will result in an improvement in
overall thermal resistance junction-to-ambient. This section
discusses those components of thermal resistance that can
be influenced by the manufacturer of the integrated circuit. It
also discusses those factors in the overall thermal resistance that can be impacted by the end user of the integrated
circuit. Understanding these issues will go a long way in
understanding chip power capabilities and what can be
done to insure the best possible operating conditions and,
thus, best overall reliability.

= TJ(max)-TA = 150'C-25'C = 198W
9JA

2.0 ",:--+---11---+-+--+---1

~ 1.6

I

la-PIN

I

t---t--+-+-MoILOEO PACKAGE

63'C/W'

8-24

Die SIze
Figure 6 shows a graph of our 16-pin DIP thermal resistance
as a function of integrated circuit die size. Clearly, as the
chip size increases the thermal resistance decreases-this
relates directly to having a larger area with which to dissipate a given power.

.. -

110
w

100

'"

~Cf~ 80
;!~~

ffi!5!o

:cto
i~

~::!.

70

TUH/9312-8

FIGURE 8. Thermal Resistance vs
Board or Socket Mount
AirFlow

3 4 5 6 78910
DIE SIZE (kMIL2)

When a high power situation exists and the ambient temperature cannot be reduced, the next best thing is to provide air
flow in the vicinity of the package. The graph of Figure 9
illustrates the impact this has on thermal resistance. This
graph plots the relative reduction in thermal resistance normalized to the still air condition for our 16-pin molded DIP.
The thermal ratings on National Semiconductor's interface
circuits data sheets relate to the still air environment.

TUH/9312-6

FIGURE 6. Thermal Resistance vs Die Size
Lead Frame Material
Figure 7 shows the influence of lead frame material (both
die attach and device pins) on thermal resistance. This
graph compares our same 16-pin DIP with a copper lead
frame, a Kovar lead frame, and finally an Alloy 42 type lead
frame-these are lead frame materials commonly used in
the industry. Obviously the thermal conductivity of the lead
frame material has a significant impact in package power
capability. Molded interface circuits from National Semiconductor use the copper lead frame exclusively.

~ii

"':IE

150

-

130

'"

....
....

-

:!5Z ..

i~
~~

~

90
70

AL~

Ii

1.0

~ 0.9

:::

~

I~

,..

O.B

,
~

0.7
0.6

DIEf"
lk MIL2
Jk1J2

rT"'1"

III

I

KpVAR

I I I 11L~N
MOLDED ~CrlE

i'

~ 0.5

D

500
1000
AIR FLOW (LINEAR FEET/MINUTE)
TL/H/9312-9

FIGURE 9. Thermal ResIstance vs Air Flow

~

Other Factors

50
1

1.1

;!

~BOARO ~~~=TMOS~~~:::

~-F5
;!~!: 110
~~o

70

SOCKET

~to-",

2
3 4 5 6 7 8 910
DIE SIZE (kMIL2)

2

w

~ ~ .....t"o

~

50

z ....
j$ffi

~

90

60

. . . . r-.,

'"

.. -

80

...

60

170

155!~
i=~
I~
~~

90

"':IE

:!5Z ..

100

;~~

w

~ffi
~a;

~8
!!!l!lli
!!ii

A number of other factors influence thennal resistance. The
most important of these is using thermal epoxy in mounting
ICs to the PC board and heat sinks. Generally these techniques are required only in the very highest of power applications.

2
345678910
DIE SIZE (kMIL2)
TL/H/9312-7

FIGURE 7. Thermal Resistance vs
Lead Frame Material

Some confusion exists between the difference in thermal
resistance junction-to-ambient (8JA) and thermal resistance
junction-to-case (8JC)' The best measure of actual junction
temperature is the junction·to-ambient number since nearly
all systems operate in an open air environment. The only
situation where thermal reSistance junction-to-case is important is when the entire system is immersed in a thermal bath
and the environmental temperature is indeed the case temperature. This is only used in extreme cases and is the exception to the rule and, for this reason, is not addressed in
this application note.

Board vs Socket Mount
One of the major paths of dissipating energy generated by
the integrated circuit is through the device leads. As a result
of this, the graph of Figure 8 comes as no surprise. This
compares the thermal resistance of our 16-pin package soldered into a printed circuit board (board mount) compared
to the same package placed in a socket (socket mount).
Adding a socket in the path between the PC board and the
device adds another stage in the thermal flow path, thus
increasing the overall thermal resistance. The thermal capabilities of National Semiconductor's interface circuits are
specified assuming board mount conditions. If the devices
are placed in a socket the thermal capabilities should be
reduced by approximately 5% to 10%.

8·25

NATIONAL SEMICONDUCTOR
PACKAGE CAPABILITIES
Figures 10 and 11 show composite plots of the thermal
characteristics of the most common package types in the
National Semiconductor Linear Circuits product family. Rgure 10 is a composite of the copper lead frame molded
package. Figure 11 is a composite of the ceramic (cavity)
DIP using poly die attach. These graphs represent board
mount still air thermal capabilities. Another, and final, thermal resistance trend will be noticed in these graphs. As the
number of device pins increase in a DIP the thermal resistance decreases. Referring back to the thermal flow chart,
this trend should, by now, be obvious.

sheets reflect a 15% safety margin from the average numbers found in this application note. Insuring that total package power remains under a specified level will guarantee
that the maximum junction temperature will not exceed the
package maximum.
The package power ratings are specified as a maximum
power at 25'C ambient with an associated derating factor
for ambient temperatures above 25'C. It is easy to determine the power capability at an elevated temperature. The
power specified at 25'C should be reduced by the derating
factor for every degree of ambient temperature above 25'C.
For example, in a given product data sheet the following will
be found:
Maximum Power Dissipation' at 25'C
Cavity Package
1509 mW
Molded Package 1476 mW

RATINGS ON INTERFACE CIRCUITS DATA SHEETS
In conclusion, all National Semiconductor Linear Products
define power dissipation (thermal) capability. This Information can be found in the Absolute Maximum Ratings section
of the data sheet. The thermal information shown in this
application note represents average data for characterization of .the indicated package. Actual thermal resistance can
vary from ± 10% to ± 15% due to fluctuations in assembly
quality, die shape, die thickness, distribution of heat sources
on the die, etc. The numbers quoted in the linear data

, Derate cavity package all 0 mWI'C above 25'C; derale molded package
al".8 mW/'C above 25'C.

If the molded package is used at a maximum ambient temperature of 70'C, the package power capability is 945 mW.
Po @ 70"C = 1476 mW - (11.8 mW I'C) X (70'C - 25'C)
= 945mW

Molded (N Package) DIP'
Copper Leadframe-HTP
Ole Attach Board MountStili Air

Cavity (J Package) DIP'
Poly Ole Attach Board
Mount-Stlll Air

138 r---r---r--r....,-""1""I"T"n

140 r---r--'-''''''-''T"T"T"n

iiI:: 1;:;::--.jl--F"'I~t-H-H
d!70~mm

iT !li

1:2.

80

30

1-;j~i-:li:-:t""-irT,

~:"":':'-EI',-",p'.. ~8"4D~4iII-++i

10 '-----'--.................~.......
2
3 4 6 & 7 8810
1

3

DIE SIZE (kMIL2).

'Packages from a. to 20'pln 0.3 mil wldlh
22·pln 0.4 mil wldlh
24· to 40-pln 0.8 mil width

TL/H/9312-10

'Packages from 8· to 20'pln 0.3 mil wldlh
22·pln 0.4 mil wldlh
24-10 48.pln 0.8 mil width

FIGURE 10. Thermal Resistance vs Ole Size
vs Package Type (Molded Package)

.......

180

~

l-

JUNE 1985

~,t=

(NARROW
SO-19-N BODY)
5o-14-W (WIlE
~~: BODY)

......... .,.....,
SO- B-N

140

r--..

120

to..

........ ~

...... i:!'

100

....

So-l4-N
so- B-N

80

-..;;;

80

lK

TLlH/9312-11

FIGURE 11. Thermal Resistance vs Ole Size
vs Package Type (Cavity Package)

DIE-SIZE (NIL2)

180

.....

4 6 8 7 8910

DIE SIZE (kMIL2)

10K

So-l4-W

~~~:

lOOK

alA- THERMAL RESISTANCE FOR "SO" PACKAGES
(BOARD MOUNT)

FIGURE 12
6-26

TL/H/9312-12

~National

~ semiconductor

APPENDIX F
How to Get the Right Information From a Data Sheet
Not All Data Sheets Am Created Alike, and False Assumptions Could Cost an Engineer Time and Money
By Robert A. Pease
When a new product arrives in the marketplace, it hopefully
will have a good, clear data sheet with it.

Every year, for the last 20 years, manufacturers have been
trying to explain, with varying success, why they do not measure the Zin per se, even though they do guarantee it.

The data sheet can show the prospective user how to apply
the device, what performance specifications are guaranteed
and various typical applications and characteristics. If the
data-sheet writer has done a good job, the user can decide
if the product will be valuable to him, exactly how well it will
be of use to him and what precautions to take to avoid
problems.

In other cases, the manufacturer may specify a test that can
be made only on the die as it is probed on the wafer, but
cannot be tested after the die is packaged because that
signal is not accessible any longer. To avoid frustrating and
confusing the customer, some manufacturers are establishing two classes of guaranteed specifications:
• The tested limit represents a test that cannot be doubted, one that is actually performed directly on 100 percent
of the devices, 100 percent of the time.

SPECIFICATIONS
The most important area of a data sheet specifies the characteristics that are guaranteed-and the test conditions that
apply when the tests are done. Ideally, all specifications that
the users will need will be spelled out clearly. If the product
is similar to existing products, one can expect the data
sheet to have a format similar to other devices.

• The design limit covers other tests that may be indirect,
implicit or simply guaranteed by the inherent design of
the device, and is unlikely to cause a failure rate (on that
test), even as high as one part per thousand.
Why was this distinction made? Not just because customers
wanted to know which specifications were guaranteed by
testing, but because the quality-assurance group insisted
that it was essential to separate the tested guarantees from
the design limits so that the AQL (assurance-quality level)
could be improved from 0.1 percent to down below
100 ppm.

But, if there are significant changes and improvements that
nobody has seen before, then the writer must clarify what is
meant by each specification. Definitions of new phrases or
characteristics may even have to be added as an appendix.
For example, when fast-settling operational amplifiers were
first introduced, some manufacturers defined settling time
as the time after slewing before the output finally enters and
stays within the error-band; but other manufacturers included the slewing time in their definition. Because both groups
made their definitions clear, the user was unlikely to be confused or misled.

Some data sheets guarantee characteristics that are quite
expensive and difficult to test (even harder than noise) such
as long-term drift (20 ppm or 50 ppm over 1,000 hours).
The data sheet may not tell the reader if it is measured,
tested or estimated. One manufacturer may perform a 100percent test, while another states, "Guaranteed by sample
testing." This is not a very comforting assurance that a part /
is good, especially in a critical case where only a long-term
test can prove if the device did meet the manufacturer's
specification. If in doubt, question the manufacturer.

However, the reader ought to be on the alert. In a few cases, the data-sheet writer is playing a specsmanship game,
and is trying to show an inferior (to some users) aspect of a
product in a light that makes it look superior (which it may
be, to a couple of users).

GUARANTEES

TYPICALS

When a data sheet specifies a guaranteed minimum value,
what does it mean? An assumption might be made that the
manufacturer has actually tested that specification and has
great confidence that no part could fail that test and still be
shipped. Yet that is not always the case.

Next to a guaranteed specification, there is likely to be another in a column labeled "typical".
It might mean that the manufacturer once actually saw one
part as good as that. It could indicate that half the parts are
better than that specification, and half will be worse. But it is
equally likely to mean that, five years ago, half the parts
were better and half worse. It could easily signify that a few
parts might be Slightly better, and a few parts a lot worse;
after all, if the noise of an amplifier is extremely close to the
theoretical limit, one cannot expect to find anything much
better than that, but there will always be a few noisy ones.

For instance, in the early days of op amps (20 years ago),
the differential-input impedance might have been guaranteed at 1 MO.-but the manufacturer obviously did not measure the impedance. When a customer inSisted, "I have to
know how you measure this impedance," it had to be explained that the impedance was not measured, but that the
base current was. The correlation between Ib and Zin permitted the substitution of this simple dc test for a rather
messy, noisy, hard-to-interpret test.

If the specification of interest happens to be the bias current
(Ib) of an op amp, a user can expect broad variations. For
example, if the specification is 200 nA maximum, there
might be many parts where Ib is 40 nA on one batch (where
the beta is high), and a month later, many parts where the Ib
is 140 nA when the beta is low.

Reprinted by permission from Electronic Engineering Times.

8-27

II.
.~

I

Absolute Maximum Ratings (Note 11)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
Supply Voltage
Output Voltage
Output Current

Lead Temp. (Soldering, 4 seconds)

+35Vto -0.2V
+6Vto -1.0V

+300"C
+ 260"C

Specified Operating Temp. Range (Note 2)

10mA

LM34C, LM34CA

TMINtoTMAX
- 50°F to + 300°F
-40"F to + 230°F

LM34D

+ 32°F to +212"F

LM34,LM34A

Storage Temperature,
TO·46 Package
TO·92 Package

*

TO·46 Package
TO·92 Package

-76"Fto +356°F
-76°F to + 300°F

DC Electrical Characteristics (Note 1, Note 6)
LM34A
Parameter

Accuracy (Note 7)

Conditions

=
=
=
=

Typical

Tested
Limit
(Note 4)

+77°F
O°F
TMAX
TMIN

±0.4
±0.6
±0.8
±0.8

Nonlinearity (Note 8)

TMIN';; TA';; TMAX

±0.35

Sensor Gain
(Average Slope)

TMIN';; TA';; TMAX

+10.0

+9.9,
+10.1

Load Regulation
(Note 3)

TA = +77"F
TMIN ,;; TA ,;; TMAX
0,;; IL';; 1 mA

±0.4
±0.5

±1.0

Line Regulation (Note 3)

TA = +77°F
5V,;; Vs';; 30V

±0,O1
±0.02

±0.05

75
131
76
132

90

Quiescent Current
(Note 9)

Change of Quiescent
Current (Note 3)

TA
TA
TA
TA

Vs
Vs
Vs
Vs

=
=
=
=

+5V, +77°F
+5V
+30V, +77"F
+30V

4V ,;; Vs ,;; 30V, + 77°F
5V,;; Vs';; 30V

Temperature Coefficient
of Quiescent Current
Minimum Temperature
for Rated Accuracy

In circuit of Figure 1,
IL = 0

Long.Term Stability

Tj

=

TMAX for 1000 hours

LM34CA
Design
Limit
(Note 5)

±1.0

Typical
±0.4
±0.6
±0.8
±0.8

±2.0
±2.0
±0.7

Tested
Limit
(Note 4)

±3.0
±0.8

OF

+10.0

+9.9,
+10.1

mVloF,min
mV/oF,max

±3.0

mVimA
mV/mA

±0.1

mVIV
mVIV

±0.01
±0.02

±0.05

±0.1

90

183

75
118
76
117

3.0

0.5
1.0

+0.30

+0.5

+3.0

+5.0

2.0

±0.16

OF
OF
OF
OF

±0.30

±1.0

+0.5
+1.0

±2.0
±2.0

±0.4
±0.5

92

Units
(Max)

±1.0

±3.0

180

Design
Limit
(Note 5)

142

/LA
/LA
!LA
/LA

3.0

/LA
!LA

+0.30

+0.5

!LA/OF

+3.0

+5.0

OF

±0.16

139
92
2.0

OF

Note 1: Unless otherwise noted,these specifications apply: -50"F ,; TI ,; + 300"F for the LM34 and LM34A; -40"F ,; TI ,; + 230"F for the LM34C and
LM34CA; and +32'F ,; TI ,;; + 212'Fforlhe LM34D. Vs = +5 Vdcand ILOAD = 50 p.A in Ihe clrcuRof F/gure2; +6 Vdcfor LM34 and LM34A for23O'F';; Tj';;
300'F. These specifications also apply from + 5'F to TMAX In the circuit of FlgUftJ 1.
Note 2: Thermal resistanca of the TO-46 package is 292'F/W Junction to ambient and 43'F/W Junction to case. Thermal resistance 01 the TO·92 package Is
324'F/W junction to ambient.
Note 3: Regulation is measured at constant junction temperature using pulse testing with a low duty cycle. Changes in output due to heating effects can be
computed by multiplying the Intemal diSSipation by the thermal resistance.
Note 4: Tested IImRB are guaranteed and 100% tested In production.
Note 5: Design IImRB are guaranteed (but not 100% production tested) over the Indicated temperature and supply voltage ranges. These IimRB are not used to
calculate outgoing quality levels.
Note 6: Specification in BOLDFACE TYPE apply over the full rated temperature range.
Note 7: Accuracy is defined as the error between the output voltage and 10 mV/'F times the device's case temperature at specified condHlons 01 voltage, curren~
and temperature (expressed In 'F).
Note 8: Nonlinearity Is defined as the deviation 01 the output·voltage-versus-temperature curve lrom the best·fit stralghlilne over the device's rated temperature
range.
Note 9: Quiescent current Is defined In the circuit of FlguftJ 1.
Note 10: Contact factory for avallabliRy 01 LM34CAZ.

**Not.

11: Absolute Maximum Ratings Indicate limits beyond which damage to the device may ocour. DC and AC electrical speCifications do not apply when

operating the device beyond Its rated operating condRions (see Note 1).

8·28

Another example is the application hint for the LF156 family:

A POint-By-Point Look

"Exceeding the negative common-mode limit on either input
will cause a reversal of the phase to output and force the
amplifier output to the corresponding high or low state. Exceeding the negative common-mode limit on both inputs will
force the amplifier output to a high state. In neither case
does a latch occur, since raising the input back within the
common-mode range again puts the input stage and, thus
the amplifier, in a normal operating mode."

Let's look a little more closely at the data sheet of the National Semiconductor LM34, which happens to be a temperature sensor.
Note 1 lists the nominal test conditions and test circuits in
which all the characteristics are defined. Some additional
test conditions are listed in the column "Conditions", but
Note 1 helps minimize the clutter.
Note 2 gives the thermal impedance, (which may also be
shown in a chart or table).

That's the kind of information a manufacturer should really
give to a data-sheet reader because no one could ever
guess it.

Note 3 warns that an output impedance test, if done with a
long pulse, could cause significant self-heating and thus,
error.

Sometimes, a writer slips a quirk into a characteristic curve,
but it's wiser to draw attention to it with a line of text. This is
because it's better to make the user sad before one gets
started, rather than when one goes into production. Conversely, if a user is going to spend more than 10 minutes
using a new product, one ought to spend a full five minutes
reading the entire data sheet.

Note 6 is intended to show which specs apply at all rated
temperatures.
Note 7 is the definition of the "Accuracy" spec, and Note 8
the definition for non-linearity. Note 9 states in what test
circuit the quiescent current is defined. Note 10 indicates
that one model of the family may not be available at the time
of printing (but happens to be available now), and Note 11 is
the definition of Absolute Max Ratings.
•

FINE PRINT
What other fine print can be found on a data sheet? Sometimes the front page may be marked "advance" or "preliminary." Then on the back page, the fine print may say something such as:

Note-the "4 seconds" soldering time is a new standard
for plastic packages.

•• Note-the wording of Note 11 has been revised-this is
the best wording we can devise, and we will use it on all
future datasheets.

"This data sheet contains preliminary limits and design
specifications. Supplemental information will be published
at a later date. The manufacturer reserves the right to make
changes in the products contained in this document in order
to improve design or performance and to supply the best
possible products. We also assume no responsibility for the
use of any circuits described herein, convey no license under any patent or other right and make no representation
that the circuits are free from patent infringement."

APPLICATIONS
Another important part of the data sheet is the applications
section. It indicates the novel and conventional ways to use
a device. Sometimes these applications are just little ideas
to tweak a reader's mind. After looking at a couple of applications, one can invent other ideas that are useful. Some
applications may be of no real interest or use.

In fact, after a device is released to the marketplace in a
preliminary status, the engineers love to make small improvements and upgrades in specifications and characteristics, and hate to degrade a specification from its first published value-but occasionally that is necessary.

In other cases, an application circuit may be the complete
definition of the system's performance; it can be the test
circuit in which the specification limits are defined, tested
and guaranteed. But, in all other instances, the performance
of a typical application circuit is not guaranteed, it is only
typical. In many circumstances, the performance may depend on external components and their precision and
matching. Some manufacturers have added a phrase to
their data sheets:

Another item in the fine print is the manufacturer's telephone number. Usually it is best to refer questions to the
local sales representative or field-applications engineer, because they may know the answer or they may be best able
to put a questioner in touch with the right person at the
factory.

"Applications for any circuits contained in this document are
for illustration purposes only and the manufacturer makes
no representation or warranty that such applications will be
suitable for the use indicated without further testing or modification."

Occasionally, the factory's applications engineers have all
the information. Other times, they have to bring in product
engineers, test engineers or marketing people. And sometimes the answer can't be generated quickly-data have to
be gathered, opinions solidified or poliCies formulated before the manufacturer can answer the question. Still, the
telephone number is the key to getting the factory to help.

In the future, manufacturers may find it necessary to add
disclaimers of this kind to avoid disappointing users with
circuits that work well, much of the time, but cannot be easily guaranteed.

ORIGINS OF DATA SHEETS

The applications section is also a good place to look for
advice on quirks-potential drawbacks or little details that
may not be so little when a user wants to know if a device
will actually deliver the expected performance.

Of course, historically, most data sheets for a class of products have been closely modeled on the data sheet of the
forerunner of that class. The first data sheet was copied to
make new versions.

For example, if a buffer can drive heavy loads and can handle fast signals cleanly (at no load), the maker isn't doing
anybody any favors if there Is no mention that the distortion
goes sky-high if the rated load is applied.

That's the way it happened with the UA709 (the first monolithic op amp) and all its copies, as well as many other similar families of circuits.

8-29

~.-----------------------------------------------------------~

~

l

Q.

C

WHEN TO WRITE DATA SHEETS

Even today, an attempt is made to build on the good things
learned from the past and add a few improvements when
necessary. But, it's important to have real improvements,
not just change for the sake of change.

A new product becomes available. The applications engineers start evaluating their application circuits and the test
engineers examine their production test eqUipment.

So, while it's not easy to get the format and everything in it
exactly right to please everybody, new data sheets are continually surfacing with new features, applications ideas,
specifications and aids for the user. And, if the users complain loudly enough about misleading or inadequate data
sheets, they can help lead the way to change data sheets.
That's how many of today's improvements came aboutthrough customer demand.

But how can the users evaluate the new device? They have
to have a data sheet-which is still in the process of being
written. Every week, as the data sheet writer tries to polish
and refine the Incipient data sheet, other engineers are reporting, "These spec limits and conditions have to be revised," and, "Those application circuits don't work like we
thought they would; we'll have one running in a couple of
days." The marketing people insist that the data sheet must
be finalized and frozen right away so that they can start
printing copies to go out with evaluation samples.
These trying conditions may explain why data sheets always
seem to have been thrown together under panic conditions
and why they have so many rough spots. Users should be
aware of the conflicting requirements: Getting a data sheet
"as completely as possible" and "as accurately as possible" is compromised if one wants to get the data sheet "as
quickly as possible."

Who writes data sheets? In some cases, a marketing person does the actual writing and engineers do the checking.
In other companies, the engineer writes, while marketing
people and other engineers check. Sometimes, a committee seems to be doing the writing. None of these ways is
necessarily wrong.
For example, one approach might be: The original designer
of the product writes the data sheet (inside his head) at the
same time the product is designed. The concept here is, if
one can't find the proper ingredients for a data sheet-good
applications, convenient features for the user and nicely
tested specifications as the part is being deSigned-then
maybe it's not a very good product until all those ingredients
are completed. Thus, the collection of raw materials for a
good data sheet is an integral part of the design of a product. The actual assembly of these materials is an art which
can take place later.

The reader should always question the manufacturer. What
are the alternatives? By not asking the right question, a misunderstanding could arise; getting angry with the manufacturer is not to anyone's advantage.

Robert Pease has been staff scientist at National Semiconductor Corp., Santa Clara, Calif., for eleven years. He has
designed numerous op amps, data converters, voltage regulators and analog-circuit functions.

i
I

8-30

.---------------------------------------------------------------,>
"'C

~National

"'C
CD
:::J
C.

~ Semiconductor

)('

b

AppendixG
Obsolete Product Replacement Guide

C'
VI

o
![
CD
"tI

(;
Some device types, individual temperature grades and package options have been discontinued. This guide is provided to help
design engineers select and specify an appropriate alternative.

C.
C

-

(")

:D

NSC Part Number

Replacement

A081200
AF100
AF121
AF134
OAC1200/1201
OH3467
OH3725
OS8627
OS8628
LF352
LF400
LF401
LF13300
LF13741
LHOOO1
LHOOO5/LHOOO5A
LHOO20
LHOO22
LHOO23
LHOO37
LHOO38
LHOO43
LHOO44
LHOO45
LHOO52
LHOO53
LHOO61
LHOO62
LHOO75
LHOO76
LHOO82
LHOO84
LHOO86
LHOO91
LH0132
LH2011
LH2101
LH2108
LH2110
LH2201A

AOC3711
None
None
None
OAC1265
None
None
None
None
LM3631
None
None
AOC3711
None
LM4250
LHOOO3
LH0101
A0506
A0585
LHOO36
None
A0583
OP07
None
OP100
None
None
HA5162
None
None
None
None
None
None
LHOO32
LM11
LM101
LM108
LM110
LM201A

Note
2

2

2

2
2
2
2
2
2
3
2
2
2

2

2
2
2
2
2
2

NSC Part Number

Replacement

LH2208
LH2208A
LH2301
LH2308
LH2310
LH4003
LH4006
LH4008
LH4009
LH4010
LH4011
LH4012
LH4033
LH4063
LH4101
LH4105
LH4106
LH4117
LH4124
LH4141
LH4161
LH4162
LH4200
LH4201
LH4266
LH4267
LH4810
LH4860
LH7001
LH7070
LH24250
LM170/270/370
LM171/271/371
LM172/272/372
LM173/273/373
LM174/274/374
LM175/275/375
LM216/316
LM363
LM388N-2/N-3
LM377N

LM208
LM208A
LM301
LM308
LM310
EL2031
CLC110
883553
883553
EL2004
None
None
LHOO33
LHOO63
LM6313
LM6218
LM6313
LM6181
LM6181
OPA654
LM6361
LM6361
CLC104
CLC104
None
None
None
None
None
LHOO70
LM11
LM13600N
None
None
None
None
None
LM11
None
LM388N-1
LM2877P

Nole 1: Pin for Pin replacemenl.
Nole 2: FUNCTIONAL REPLACEMENT: Consult datasheet to determine suitability of the replacement for specific application.
Nole 3: SIMILAR DEVICE with superior performance: Consult datasheet to determine suitability of the replacement for specific application.

8-31

Note
2
2
2
2
2
2
2
2
2
2

2
2
2
2
2
2
2
2
2
2
2
2

2
2
2

2
2
3

CD
"'C

iii
(")
CD

3

-c:
CD
:::J

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C

CD

m r-----------------------------------------------------------------------------,

'a

'3

-

CJ

c
m

~National

~ Semiconductor

E

g
'is.
m

a:
U
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'a

e

111.

li
.§

J
.!5

'a
C

m

a.

~

NSC Part Number

Replacement

LM378N
LM379
LM322H
LM565CH
LM567CH
LM592
LM733
LM776
LM1014
LM1017
LM1019
LM1800
LM1801
LM1822
LM1812
LM1837
LM1863
LM1866
LM1870
LM1871
LM1872

LM2878P
LM2879T
LM122H
LM565H
LM567H
None
None
None
None
None
None
None
None
LM1823
None
None
LM1868
None
None
None
None

Note

NSC Part Number

3
3
2
2
2

LM1877N-11N-21N-3
LM1880
LM1884
LM1889
LM1895
LM1897
LM1965
LM2002
LM2005
LM2065
LM2895
LM2905N
LM3011
LM3064
LM3075
LM3820
LM4500
LM776
LMC669
MHOOO7
MM54240

3

3

Replacement

LM1877N-9
None
None
None
LM1896
None
LM1865
None
None
LM1865
LM2896
LM3905N
None
None
None
None
None
None
None
CTSOOO7
None

Note t: Pin for Pin replacement
Note 2: FUNCTIONAL REPLACEMENT: Consult datasheet to determine suitability of the replacement for specific application.
Note 3: SIMILAR DEVICE with superior performance: Consult datasheet to determine suitability of the replacement for specific application.

8-32

Note

2

3
3

3
3
2

1

.

lao
Z

Appendix H
Safe Operating Areas for
Peripheral Drivers

National Semiconductor
Application Note 213
Bill Fowler

Peripheral Drivers is a broad definition given to Interface
Power devices. The devices generally have open-collector
output transistors that can switch hundreds of milliamps at
high voltage, and are driven by standard Digital Logic gates.
They serve many applications such as: Relay Drivers, Printer Hammer Drivers, Lamp Drivers, Bus Drivers, Core Memory Drivers, Voltage Level Transistors, and etc. Most IC devices have a specified maximum load such as one TTL gate
can drive ten other TTL gates. Peripheral drivers have many
varied load situations depending on the application, and requires the design engineer to interpret the limitations of the
device vs its application. The major considerations are Peak
Current, Breakdown Voltage, and Power Dissipation.

times measured in an Inductive Latch-Up Test). Observe
that all breakdown voltages converge on LVCEO at high
currents, and that destructive secondary breakdown voltage
occurred (shown as dotted line) at high currents and high
voltage corresponding to exceeding the power dissipation
of the device. The characteristics of secondary breakdown
voltage vary with the length of time the condition exists,
device temperature, voltage, and current.

....

N

(0)

OUTPUT CURRENT AND VOLTAGE CHARACTERISTICS
Figure 1 shows the circuit of a typical peripheral driver, the
DS75451. The circuit is equivalent to a TTL gate driving a
300 mA output transistor. Figure 2 shows the characteristics
of the output transistor when it is ON and when it is OFF.
The output transistor is capable of sinking more than one
amp of current when it is ON, and is specified at a VOL =
0.7V at 300 mAo The output transistor is also specified to
operate with voltages up to 30V without breaking down, but
there is more to that as shown by the breakdown voltages
labeled BVCES, BVCER, and LVCEO.

Vee

vee

OUTPUT ON

OUTPUT
SATURATED
3DDmA

vee
~----------------~~-=~~--~VCE

VOL
TL/F/5860-2

FIGURE 2. Output Characteristics ON and OFF
OUTPUT TRANSFER CHARACTERISTICS VS
INDUCTIVE AND CAPACITIVE LOADS

INPUT A " ' - - - - "
INPUT B

0--+-'"

TL/F/5860-1

FIGURE 1. Typical Peripheral Driver DS75451
BVCES corresponds to the breakdown voltage when the
output transistor is held off by the lower output transistor of
the TTL gate, as would happen if the power supply (Vecl
was 5V. BVCER corresponds to the breakdown voltage
when the output transistor is held off by the 500 resistor, as
would happen if the power supply (Vecl was off (OV).
LVCEO corresponds to the breakdown voltage of the output
transistor if it could be measured with the base open.
LVCEO can be measured by exceeding the breakdown volt·
age BVCES and measuring the voltage at output currents of
1 to 10 mA on a transistor curve tracer (LVCEO is some-

Figure 3 shows the switching transfer characteristics superimposed on the DC characteristics of the output transistor
for an inductive load. Figure 4 shows the switching transfer
characteristics for a capacitor load. In both cases in these
examples, the load voltage (VB) exceeds LVCEO. When the
output transistor turns on with an inductive load the initial
current through the load is a mA, and the transfer curve
switches across to the left (Vou and slowly charges the
inductor. When the output transistor turns off with an inductive load, the initial current is IOL' which is sustained by the
inductor and the transistor curve switches across to the
right (VB) through a high current and high voltage area
which exceeds LVCEO and instead of turning off (shown as
dotted line) the device goes into secondary breakdown. It is
generally not a good practice to let the output transistor's
voltage exceed LVCEO with an inductive load.
In a similar case with a capacitive load shown in Figure 4,
the switching transfer characteristics rotate counter-clockwise through the DC characteristics, unlike the inductive
load which rotated clockwise. Even though the switching
transfer curve exceeds LVCEO, it didn't go into secondary
breakdown. Therefore, it is an acceptable practice to let the
output transistor voltage exceed LVCEO, but not exceed
BVCER with a capacitive load.

8-33

... ,-----------------------------------------------------------------------------,
~

i

Figure 6 shows the switching transfer characteristics of a
capacitive load which leads to secondary breakdown. This
condition occurs due to high sustained currents, not breakdown voltage. In this example, the large capacitor prevented the output transistor from switching fast enough through
the high current and high voltage region; in turn the power
dissipation of the device was exceeded and the output transistor went into secondary breakdown.

Va

IOL
VB

IL.......::::::====-*==.....VaIi=!.-='- VeE

7

TLIFISB80-3

ON

FIGURE 3. Inductive Load Transfer Characteristics

...

1L......;::---~

VB

_oI.-_--'-_~VeE

VB

TLIFIS8BO-8

FIGURE 6. Capacitive Load Transfer Characteristics
Figure 7 shows another method of quenching the Inductive
voltage spike caused by the Initial' Inductive current. This
method dampens the switching response by the addition of
Ro and Co. The values of Ro and CD are chosen to critically
dampen the values of RL and. LL; this will limit the output
voltage to 2 X Ve.
LL
(RL + Ro) x VLLCi) s: 0.5

IOL

rr

OFF

Il..-=======......Jt.._.'-__ VeE
Va

Va
TLlFI5BBO-4

FIGURE 4. Capacitive Load Transfer CharacteristiCS
Figure 5 shows an acceptable application with an Inductive
load. The load voltage (Ve) Is less than LVCEO, and the
Inductive voltage spike caused by the initial Inductive current is quenched by a diode connected to Ve.

Ie
VB

TLIFISBBO-7

FIGURE 7. Inductive Load Dampened by Capacitor
Figure 8 shows a method of reducing high sustaining currents in a capacitive load. Ro in series with the capacitor
(CLl will limit the switching transistor without affecting final
amplitude of the output voltage, since the IR drop across Ro
will be zero after the capacitor is charged.
As an additional warning, beware of parasitic reactance. If
the driver'S load is located some distance from the driver
(as an example: on the Inclosure panel or through a con-

1L-....:::::::=--...-----~--VeE
TLIFI5BBO-5

FIGURE 5. Inductive Load Transfer Characteristics
Clamped by Diode
8-34

necting cable) there will be additional inductance and capacitance which may cause ringing on the driver output
which will exceed LVCEO or transient current that exceeds
the sustaining current of the driver. A 300 mA current
through a small inductor can cause a good size transient
voltage, as compared with 20 mA transient current observed with TIL gates. For no other reason than to reduce
the noise associated with these transients, it is good practice to dampen the driver's output.

device, and the power on the output of the device due to the
Driver Load.

....

>Z
N

Co)

POWER LIMITATIONS OF PACKAGE
Figure 9 shows the equivalent circuit of a typical power device in its application. Power is shown equivalent to electrical current, thermal resistance is shown equivalent to electrical resistance, the electrical reactance C and L are equivalent to the capacity to store heat, and the propagation delay through the medium. There are two mediums of heat
transfer: conduction through mass and radiant convection.
Convection is insignificant compared with conduction and
isn't shown in the thermal resistance Circuits. From the pOint
power is generated (device junction) there are three possible paths to the ultimate heat sink: 1) through the device
leads; 2) through the device surface by mechanical connection; and 3) through the device surface to ambient air. In all
cases, the thermal paths are like delay lines and have a
corresponding propagation delay. The thermal resistance is
proportional to the length divided by the cross sectional
area of the material. The Thermal Inductance is proportional
to the length of the material (copper, molding compound,
etc.) and inversely proportional to the cross sectional area.
The thermal capacity is proportional to the volume of the
material.

In conclusion, transient voltage associated with inductive
loads can damage the peripheral driver, and transient currents associated with capacitive loads can also damage the
driver. In some instances the device may not exhibit failure
with the first switching cycle, but its conditions from ON to
OFF will worsen after many cycles. In some cases the device will recover after the power has been turned off, but its
long term reliability may have been degraded.
POWER DISSIPATION
Power Dissipation is limited by the IC Package Thermal
Reactance and the external thermal reactance of the environment (PC board, heat sink, Circulating air, etc.). Also, the
power dissipation is limited by the maximum allowable junction temperature of the device. There are two contributions
to the power: the internal bias currents and voltage of the
Va

TLIF/5860-8

FIGURE 8. Capacitive Load with Current Limiting Resistor

TpC BOARD

TAMBIENT

TJUNCTION

TAMBIENT

TLIF/5860-9

FIGURE 9. Thermal Reactance from Junction to Ambient

8-35

-~ r-----------------------------------------------------------------------------,
~

Device Package

N

1.4

g
DIE
PAD

DIE SIZE = &ODD MIL2

1.2

'"

co

~

[==~~~~~::]

ji

co
a:

0.8
0.6

!j; OA

2

0.2
DEVICE
PIN

50

TLIF15B60-10

100

125

160
TUF15B60-12

FIGURE 12. Maximum Package Rating Copper vs
Kovar Lead Frame Packages
Figure 11 shows that 14 pin packages have less thermal
resistance than 8 pin packages; which should be expected
since it has more pins to conduct heat and has more surface area. Something that may not be expected is that the
Thermal Resistance of the molded devices is comparable to
the ceramic devices. The reason for the lower thermal resistance of the molded devices is the Copper lead frame,
which is a better thermal conductor than the Kovar lead
frame of the ceramic package. Almost all the peripheral
drivers made by National Semiconductor are constructed
with Copper lead frames (refer to cf>JA on the specific devices data sheet). The difference between the thermal resistance of Copper and Kovar in a molded package is shown in

2.0

\.8

~

76

AMBIENT TEMPERATURE re)

FIGURE 10. Components of Thermal Reactance
for a TypicallC Package
National Semiconductor specifies the thermal resistance
from device junction through the device leads soldered in a
small PC board, measured in one cubic foot of still air. Figure 11 shows the maximum package power rating for an 8
pin Molded, an 8 pin Ceramic, 14 pin Molded and a 14 pin
Ceramic package. The slope of the line corresponds to thermal resistance (cf>JA = boP/boT).

1.6

z

1.4

~

1.2

~

1

i:i
a:

O.B

Figure 12.

0.6

Another variance in thermal resistance is the size of the IC
die. If the contact area to the lead frame is greater, then the
thermal resistance from the Die to the Lead Frame is reduced. This is shown in Figure 13. The thermal resistance
shown in Figure 11 corresponds to die that are 6000 mil2 in
area.

co

.
w

==
co

0.4
0.2
0
25

50

15

100

125

AMBIENT TEMPERATURE

150

115

re)
TLIF15B60-11

140

FIGURE 11. Maximum Package Power Rating
The maximum allowable junction temperature for ceramic
packages is 175'C; operation above this temperature will
reduce the reliability and life of the device below an acceptable level. At a temperature of 500'C the aluminum metallization paths on the die start to melt. The maximum allowable junction temperature for a molded device is 150'C, operations above this may cause the difference in thermal expansion between the molding compound and package lead
frame to sheer off the wire bonds from the die to the package lead. The industry standard for a molded device is
150'C, but National further recommends operation below
135'C if the device in its application will encounter a lot of
thermal cycling (such as powered on and off over its life).
The way to determine the maximum allowable power dissipation from Figure 11, is to project a line from the maximum
ambient temperature (TA) of the application vertically
(shown dotted in Figure 12), until the line intercepts the diagonal line of the package type, and then project a line
(shown dotted) horizontally until the line intercepts the Power Dissipation Axis (PMAX).

~ 120

~

i

80

a:

80

i

40

i!:

20

....

""'-

100

-- -......
....

o
lk

2k

5k

10k

DIE SIZE (MIL2)
TLIF15B60-13

FIGURE 13. Thermal Resistance vs Ole Size
In most applications the prime medium for heat conduction
is through the device leads to the PC board, but the thermal
resistance can be significantly improved by cooling air driven across the surface of the package. The conduction to air
is limited by a stagnant film of air at the surface of the package. The film acts as an additional thermal resistance. The
thickness of the film is proportional to its resistance. The
thickness of the film is reduced by the velocity of the air

8-36

across the package as shown in Figure 14. In most cases,
the thermal resistance is reduced 25% to 250 linear feet/
min, and 30% at 500 linear feet!min, above 500 linear feet!
min the improvement flattens out.
§:
w

~

0.8

iii0:

0.6

~

~

ffi

=
...

0.4

>

0.2

f\. I'-.

This capacity is shown as a capacitor in Figure 9. In the lab
(under a microscope) a device may be observed to glow
orange around the parameter of the junction under excessive peak power without damage to the device. Figure 15
shows a plot of maximum peak power vs applied time for
the 053654, and the same information plotted as energy vs
applied time. To obtain these curves, the device leakage
current when it switches off was used to monitor device
limitation. Note in Figure 15 there is a transition in the curve
about 10 )J-s. At this pOint, the thermal capacity of the die
has been exceeded. The thermal delay to the next thermal
capacity (the package) was too long, and limited the peak
power. These levels are not suggested operating levels, but
an example of a Peripheral Driver to handle peak transient
power.

I'-- I-

w

~
0:

o

o

500

100

lk

PEAK POWER (WATISI

AIR flOW (LINEAR FEET/MINI
TL/F/S8S0-14

FIGURE 14. Thermal Resistance vs Air Velocity
The thermal resistance can also be improved by connecting
the package to the PC board copper or by attaching metal
wings to the package. The improvement by these means is
outside the control of the IC manufacturer, but is available
from the manufacturer of the heat sink device. If the IC is
mounted in a socket rather than soldered to a PC board, the
thermal resistance through the device leads will worsen. In
most cases, the thermal resistance is increased by 20%;
again this is a variable subject to the specific socket type.

10-3IIi

EINEn~ (JrUmIX

~
0.01
I

10

100

Ik

10k

(APPLIED TIME ""I
TL/F/S8eO-1S

The maximum package rating shown in this note corresponds to a 90% confidence level that the package will
have thermal resistance equal to or less than the value
shown. The thermal resistance varies ± 5% about the mean
due to variables in assembly and package material.

FIGURE 15. Peak Power and Energy vs the
Period of Time the Power was Applied
To calculate power dissipation, the only information available to the design engineer is the parametric limits in the
device data sheet, and the same information about the load
reactance. If the calculations indicate the device is within its
limits of power dissipation, then using those parametric lim·
its is satisfactory. If the calculation of power dissipation is
marginal, the parametric limits used in the calculations
might be worst case at low temperature instead of high temperature due to a positive temperature coefficient (Tcl of
resistance. IC resistors and resistors associated with the
load generally have a positive Tc. On the other hand, diodes
and transistor emitter base voltages have a negative Tc;
which may in some circuits negate the effect of the resistors
T c. Peripheral output transistors have a positive Tc associated with VOL; while output Darlington transistors have a
negative Teat low currents and may be flat at high currents.
Figure 16 shows an example of power dissipation vs temperature; note that the power dissipation at the application's
maximum temperature (TA) was less than the power dissipation at lower temperatures. Since maximum junction temperature is the concern of the calculation, then maximum
ambient temperature power should be used. The junction
temperature may be determined by projecting a line (shown
dotted in Figure 16), with a slope proportional to JA back to
the horizontal axis (shown as TJ). If the pOint is below the
curve then TJ will be less than 150·C. TJ must not exceed
the maximum junction temperature for that package type. In
this example, TJ is less than 150'C as required by a molded
package. To calculate the power vs temperature, it is necessary to characterize the device parameters vs temperature.
Unfortunately, this information is not always provided by IC
manufacturers in the device data sheets. A method to calcu-

CALCULATIONS OF POWER DISSIPATION
Most IC devices (such as T2L) operate at power levels well
below the device package rating, but peripheral drivers can
easily be used at power levels that exceed the package
rating unknowingly, if the power dissipation isn't calculated.
As an example, the 053654 Ten Bit Printer Driver could
dissipate 3 watts (DC and, even more AC), and it is only in a
0.8 watt package. In this example, the device would be destroyed in moments, and may even burn a hole in the PC
board it is mounted on. The 053654 data sheet indicated
that the 10 outputs could sink 300 mA with a VOL of 1 volt,
but it wasn't intended that all the outputs would be sinking
this current at the same time, and if so, not for a long period.
The use of the 053654 requires that the power be calculated vs the duty cycle of the outputs.
The DC power dissipation is pretty obvious, but in another
example, a customer used the 053686 relay driver to drive
6.5h inductive load. The 053687 has an internal clamp network to quench the inductive back swing at 60V. At 5 Hz the
device dissipates 2 watts, with transient peaks up to 11
watts. After 15 minutes of operation, the driver succumbs to
thermal overload and becomes non-functional. The 053687
was intended for telephone relay, which in most applications
switches 20 times a day.
Peripheral driver will dissipate peak power levels that greatly
exceed the average DC power. This is due to the capacity of
the die and package to consume the transient energy while
still maintaining the junction temperature at a safe level.

8·37

.... ,-----------------------------------------------------------------------------,
late Icc vs temperature is to measure a device, then normalRefer to Figure 18 voltage and current waveforms corre~

z~
c

ize the measurements vs the typical value for Icc in the data
sheet, then worst case the measurements by adding 30%.
Thirty percent is normally the worst-case resistor tolerance
that IC devices are manufactured to.

sponding to the power dissipation calculated for this example of an inductive load.
PON = Average power dissipation in device output
when device is ON during total period (T)

lAr-----r--,.---.---r------.
T

~
...

'"co;::

:f

~

a:
~

1.2

= LL = ~ = 41.7 ms
RL
1200

IL = VB - VOL = 30 - 1.5 = 237.5 mA
RL
120
Ip = IL (1 - e -TONI,)

D.I
0.8

Ip = 237.5 mA (1 - e-100ms/41.7 ms)

OA

Ip = 215.9mA

Ii! 0.2
&0

7&

100

125

TON [
PON = VOL X IL X 1T

1&0

fToNe-IITdt]
--•

TON

TON [
T
-TONI, ]
PON = VOL X IL X 1- (1 - e
)
T
TON

TEMPERATURE reI

TUF/5860-16

FIGURE 16. IC Power Dissipation vs Temperature

100 [
41.7
]
PON = 1.5x237.5mAx 200 1-100 (1-e-100/41.7)

CALCULATION OF OUTPUT POWER WITH
AN INDUCTIVE LOAD

PON = 110.6 mW
POFF = Average power dissipation in device output when
device is OFF during total period (T)

For this example, the device output circuit is similar to the
DS3654 (10-Bit Printer Solenoid Driver) and the DS3686
and DS3687 (Telephone Relay Driver) as shown in Figure
17. Special features of the circuit type are the Darlington
output transistors 01 and 02 and the zener diode from the
collector of 01 to the base of 02. The Darlington output
requires very little drive from the logic gate driving it and in
turn dissipates less power when the output is turned ON and
OFF, than a single saturating transistor output would. The
zener diode (Dz) quenches the inductive backswing when
the output is turned OFF.
Device and Load Characteristics Used for
Power Calculation
Output Voltage ON
1.5V
VOL
65V
Output Clamp Voltage
Vc
Load Voltage
30V
VB
Load Resistance
1200
RL
Load Inductance
5h
LL
Period ON
100ms
TON
Period OFF
100ms
TOFF
T
Total Period
200ms

IR = Vc - VB = 65 - 30 = 291.7 mA
RL
1200
Ip + IR)
tx = Tin ( --IR215.9 + 291.7)
tx =41.7msln (
291.7
=23.1ms
POFF = Vc x

tx [
fIX e- tlT dt T
(Ip + IR) • ---tx-

tx [
POFF = Vc X - (Ip
T

+ IR)

T

x s-(1 - e
tx

23.1 [
POFF = 65 x 200 (215.9 mA

]

IR

-lxI,

) -IR

]

41.7

+ 291.7 mAl 23.1

(1 - e-23.1/41.7) - 291.7 mA]
POFF = 736mW
Po = Average power dissipation in device output
Po = PON + POFF = 110.6 + 736 = 846.6 mW
In the above example, driving a 1200 inductive load at 5 Hz,
the power dissipation exceeded a more simple calculation
of power dissipation, which would have been:

Va

Po = VOL (VB - voLl X TON
RL
T
P = 1.5 (30 - 1.5) x 100 ms = 182.5 mW
120
200ms
o
An error 460% would have occurred by not including the
reactive load. The total power dissipation must also include
other outputs (if the device has more than one output), and
the power dissipation due to the device power supply currents. This is an example where the load will most likely
exceed the device package rating. If the load is fixed, the
power can be reduced by changing the period (T) and duty
rate (TON/TOFF).

'::"

'::"

TUF/5860-17

FIGURE 17. Peripheral Driver with Inductive Load
8-38

»
z
I

N
.....

-ti5V

(0)

'"

.'"'"
~

-

IX

I-

>

....
=
~

..

-30V -

I.SV

::0 /
0

....

:Ii
a:

..=5
a:

100 m.

o 1

.

=

o L-l--J.--I.---L.---L.-L--'-....L......L..-I
o 1 2 3 4 5 6 7 8 9 10
LAMP VOLTAGE (V)
TL/F/S8S0-20

FIGURE 20. DC Characteristics of an Incandescent
Lamp

1:-,- - - 1
1

1

o

1=

20D ms

100m.

,

,

Figure 21 shows the transient response of a driver similar to
a 0875451 driving the lamp characterized in Figures 19 and
20. The equivalent load doesn't include the reactance of the
lamp base to ambient, which has a 250 ms time constant,
since 10 ms to an IC is equivalent to DC. The peak transient
current was 1 amp, settling to 200 ms, with an 8 ms time
constant. Observe the peak current is clamped at 1 amp, by
the sinking ability of the driver; otherwise the peak current
may have been 1.2 amps. The 0875451 is only rated at 300
mA, but it is reasonable to assume it could sink 1 amp be·
cause of the designed force f3 required for switching reo
sponse and worst case operating temperature.

200 m.

\,

' ...... ......

IR------------------------------TL/F/S8S0-18

FIGURE 18. Voltage and Current Waveforms
Corresponding to Inductive Load
CALCULATION OF OUTPUT POWER
WITH AN INCANDESCENT LAMP
An incandescent lamp is equivalent to a reactive load. The
reactance is related to the period of time required to heat
the lamp and the filaments positive temperature coefficient
of resistance. Figure 19 shows the transient response for a
typical lamp used on instrument panels, and the equivalent
electrical model for the lamp. Much like IC packages the
lamp has a thermal circuit and its associated propagation
delay. This lamp filament has an 8 ms time constant, and a
longer 250 ms time constant from the lamp body to ambient.
The DC characteristics are shown in Figure 20. Note the
knee in the characteristics at 2 volts; this is where power
starts to be dissipated in the form of light. This subject is
important, since more peripheral drivers are damaged by
lamps than any other load.

1
0.8

~
::E

.'$.

....z
w

a:

0.6

~~'

1122 "F

::0

0.4

0:

=
....

0.2

T

=8 ms

0-

o

10

20

30

40

50

TIME (m,)
TL/F/S8S0-21

iii

30

.
z

20

in
w
a:

10

/~

::E
:z:

'"
In

I-

~

E

w

--

FIGURE 21. Transient Incandescent Lamp Current
Calculation of the energy disSipated by a peripheral driver
for the transient lamp current shown in Figure 21 is shown
above, and the plot of energy vs time is shown in Figure 22.
Figure 22 also includes as a reference the maximum peak
energy from Figure 15. It can be seen from Figure 22 that in
this example there is a good safety margin between the
lamp load and the reference max peak energy. If there were
more drivers than one per package under the same load,
the margin would have been reduced. Also, if the peripheral
driver couldn't saturate because it couldn't sink the peak
transient lamp current, then the energy would also reduce
the margin of safe operation.

rr-

t

J-

L-

r-

38

,1141:,18

2100"F T

T

1122"F

....

O'--'----~~--~-

o

10 20 30 40 50 60 70 80 90 100

TIME (m.)
TL/F/S8S0-19

FIGURE 19. Transient Response of
an Incandescent Lamp

8·39

.,...

.

C')

N

100

Z

VB = 6.3V

c(

Cj';

.
!!!

III
10 FPEAk '~NERGY
REFERENCE

i."

=>
co

::!

>
a:
w

'"z
w

INCANDESCENT
LAMP LOAD

RB Rs

0.1

~

100

6.a-l)
(- Isn

~

95.4 ::: loon

I

0.01
10

100

lk

10k

lOOk

TLlF/5860-23

FIGURE 23_ Circuit Used to Reduce Peak
Transient Lamp Current

TIME (PS)
TLlF/5860-22

FIGURE 22. Energy vs Time for a Peripheral
Driver with an Incandescent Lamp Load

PERIPHERAL DRIVER SECTION
National Semiconductor has a wide selection of peripheral
drivers as shown in this section's guide. The DS75451,
DS75461, DS3631 and the DS3611 series have the same
selection of logic function in an 8-pin package. The
DS75461 is a high voltage selection of the DS75451 and
may switch slower. The DS3611 and DS3631 are very high
voltage circuits and were intended for slow relay applications. The DS3680, DS3686, and DS3687 were intended for
56V telephone relay applications. The DS3654 contains a
10-bit shift register followed by ten 250 mA clamped drivers.
The DS3654 was intended for printer solenoid applications.

CALCULATION OF ENERGY IN AN
INCANDESCENT LAMP
Energy =

f:

VOL (IRI

+ IR2) dt

VB - VOL
.
'RI =
R1
= IRI
iR2 = (VB ;2VOL ) e-tlT
= IR2 e- tlT

Energy =
Given:

f:

VOL (IRI

T = R2C2

+ IR2 e- tlT ) dt

= VOL liRlt + IR2T (i - e- tlT )]
VOL = 0.6V
IRI = 0.2 Amps

IRI + IR2 = 1 Amp
A common technique used to reduce the 10 to 1 peak to DC
transient lamp current is to bias the lamp partially ON, so
the lamp filament is warm. This can be accomplished as
shown in Figure 23. From Figure 20 it can be seen that the
lamp resistance at OV is 5.70, but at 1V the resistance is
18!l. At 1V the lamp dosen't start to emit light. Using a lamp
resistance of 1000 and lamp voltage of 1V, RB was calculated to be approximately 1000. This circuit will reduce the
peak lamp current from 1 amp to 316 mA.

High current and high voltage peripheral drivers find many
applications associated with digital systems, and it is the
intention of the application note to insure that reliability and
service life of peripheral drivers equal or exceed the performance of the other logic gates made by National.
For additional information, please contact the Interface Marketing Department at National or one of the many field application engineers world-wide.

8-40

~National

~ Semiconductor

All dimensions are in inches (millimeters)

20 Terminal Ceramic Leadless Chip Carrier (LCC)
NS Package Number E20A
O.200±D.OOS
(5.08D±0127!

18.890±0.203)
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3 Lead (0.200" Diameter P.C.) Metal Can Package (H)
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(4.191-4.699)
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H08C(REV E)

8-42

10 Lead (0.230" Diameter P.C.) TO-100 Metal Can Package (H)
NS Package Number H10C
0.350-0.370
+-18.890
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0.165-0.185
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8-43

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8-52

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NS Package Number N16E

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PIN NO. !----'~'F.T;;;;:;""";;O;=:;;;;;O~'!'FF.fJ
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8·54

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0.480-0.520

1,-;~ ""T"
r

1.208

130'j31./

V

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V

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0.285-0.315

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17.239-8.0011

k- ,~~-, 1~~"

0.048-0.050
11.188-1.270,-

;r::01~~,~~~

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I

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010

0.02'-0.028 7YP IBEFORE
10.810-0.7111 lEAD ANISKI

1-1- 1:::::=i~1 TYP

0.37& +0.015
-0.005

I+-

,::!::=::::,

PO~"'REVF)

4 Lead TO-202 Molded Package (P)
NS Package Number P04A
0.110:1:0.010
11.810±0.IS'1

T

~

.m~'~I--+_"""'Ii
0.2B8±0.D1I

ii.3iOffiiij

O.m 0.011

"L
0.023 -0.031
(O.884-0.7I21

0.031 ±O.OOI
10.81a±0.1271
O.IDOnOlO

j2.iiffiffij

0.021 ±0.D03

iD.5iffi07ii

-II

I

0.OS3 ±0.01&
\<>-ll.341±0.1811
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8·55

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C

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3 Lead TO-220 Molded Package (T)
NS Package Number T03B

E

is

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Do

j4---t-

0.151± 0.DD2

0.180 ± 0.005
(4.572±0.1271

--J

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l-~
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0.110±D.Olo

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0.250 !a.ol0

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1.D2D±0.DI5

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0.055xO.015
(1.397xO.3811
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0.34D±0.0ID
(B.&36 ± 0.2541

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0.03aO.DD5

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.540±O.015

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0.395

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(0.381

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'-D'-B'

(3.683±0.381)

01150
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0.1DO±0.010

0.015 ~~:~~~

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TAPERED I'. 2 SIDES

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0.2DO±0.010
(5.DB±D.2S41

T03B (FlEV K)

5 Lead TO-220 Molded Package (T)
NS Package Number T05A

r

E

D.395-OA2o

~-/~DIA
(3.B35 .0.051)

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0.250

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0.180.0.005
(4.572 .0.1271
0.050 .0.002
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1.020'0.015

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0.340 .0.010
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0.540 .0.015

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-0.016
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(2.6&7~~~m

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(1.702 '0.127)

T05A!flEVHj

8-56

5 Lead TO-220 Molded Package (T)
NS Package Number T05D
0.110tO.Ol0
2.79 t 0.25


Source Exif Data: 
File Type                       : PDF
File Type Extension             : pdf
MIME Type                       : application/pdf
PDF Version                     : 1.3
Linearized                      : No
XMP Toolkit                     : Adobe XMP Core 4.2.1-c041 52.342996, 2008/05/07-21:37:19
Create Date                     : 2017:07:04 15:55:39-08:00
Modify Date                     : 2017:07:04 16:49:44-07:00
Metadata Date                   : 2017:07:04 16:49:44-07:00
Producer                        : Adobe Acrobat 9.0 Paper Capture Plug-in
Format                          : application/pdf
Document ID                     : uuid:028df142-f9f4-a040-babd-d706c435651a
Instance ID                     : uuid:163ac397-249c-4945-a140-b053ad0b792e
Page Layout                     : SinglePage
Page Mode                       : UseNone
Page Count                      : 796


EXIF Metadata provided by EXIF.tools

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