AP65101 Datasheet. Www.s Manuals.com. R1 2 Diodes

User Manual: Marking of electronic components, SMD Codes RA, RA**, RA***, RA-, RA1, RA4, RA7, RAT, RAW, RAp, RAt, Ra. Datasheets AP65101WU-7, BAV70, BAV99, BAW56, BD53E43G, BZB84-B36, MMSTA28, RP130K121A, SSTA28, Si1553DL.

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AP65101

Document number: DS38098 Rev. 1 - 2

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AP65101

TSOT26 LIGHT LOAD IMPROVED 1.5A SYNCH DC/DC BUCK CONVERTER

Description

The AP65101 is a 500kHz switching frequency internal compensated

synchronous DC-DC buck converter. It has integrated low RDSON high

and low side MOSFETs.

The AP65101 enables continuous load current of up to 1.5A with

efficiency as high as 97%.

The AP65101 implements an automatic custom light-load efficiency

improvement algorithm.

The AP65101 features current mode control operation, which enables

fast transient response times and easy loop stabilization.

The AP65101 simplifies board layout and reduces space

requirements with its high level of integration and minimal need for

external components, making it ideal for distributed power

architectures.

The AP65101 is available in a standard Green TSOT26 package and

is RoHS compliant.

Features

 VIN 4.5V to 16V

 1.5A Continuous Output Current, 2.5A Peak

 Efficiency Up to 97%

 Automated Light Load improvement

 VOUT Adjustable from 0.8V

 500kHz Switching Frequency

 Internal Soft-Start

 Enable Pin

 Overcurrent Protection (OCP) with Hiccup

 Thermal Protection

 Totally Lead-Free & Fully RoHS Compliant (Notes 1 & 2)

 Halogen and Antimony Free. “Green” Device (Note 3)

Pin Assignments

TSOT26

Top View

3

2

1 6

4

5

IN

GND

SW

FB

EN

BST

Applications

 Gaming Consoles

 Flat Screen TV Sets and Monitors

 Set-Top Boxes

 Distributed Power Systems

 Home Audio

 Consumer Electronics

 Network Systems

 FPGA, DSP and ASIC Supplies

 Green Electronics

Notes: 1. No purposely added lead. Fully EU Directive 2002/95/EC (RoHS) & 2011/65/EU (RoHS 2) compliant.

2. See http://www.diodes.com/quality/lead_free.html for more information about Diodes Incorporated’s definitions of Halogen- and Antimony-free, "Green"

and Lead-free.

3. Halogen- and Antimony-free "Green” products are defined as those which contain <900ppm bromine, <900ppm chlorine (<1500ppm total Br + Cl) and

<1000ppm antimony compounds.

Typical Applications Circuit

Efficiency

AP65101

L1

6.5μH

R1

40.2kΩ

R2

13kΩ

C5

1µF

C2

22μF

C1

22μF

ON

OFF

1

IN

5

EN

3

SW

4

BST

6

FB

2

GND

INPUT

OUTPUT

VOUT

3.3V

VIN

12V

R3

59kΩ

Figure 1. Typical Application Circuit

Vin=4.7V

Vin=12V

Vin=16V

AP65101

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AP65101

Pin Descriptions

Pin

Name

Pin Number

Function

TSOT26

IN

1

Power Input. IN supplies the power to the IC, as well as the step-down converter switches. Drive IN with a 4.5V

to 16V power source. Bypass IN to GND with a suitably large capacitor to eliminate noise on the input to the IC.

See Input Capacitor.

GND

2

Ground

SW

3

Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC

filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch.

BST

4

High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET a 0.01µF or

greater capacitor from SW to BS to power the high side switch.

EN

5

Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator; low to

turn it off. Attach to IN with a 100kΩ pull up resistor for automatic startup.

FB

6

Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistive voltage divider

connected to it from the output voltage. The feedback threshold is 0.8V. See Setting the Output Voltage.

Functional Block Diagram

E

+

-

+

-

+

-

+

1.1V

0.3 V

INTERNAL

REFERENCE

Logic

0.8V

+

-

Internal

SS

+

-

OSCILLATOR

CURRENT

SENSE

AMPLIFIER

OVP

RAMP

CLK

CURRENT

COMPARATOR

FB

EN

0.8 V

GND

SW

BST

IN

500KHz

0.3V

1.1V

Vcc

REGULATOR

AP65101

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AP65101

Absolute Maximum Ratings (Note 4) (@TA = +25°C, unless otherwise specified.)

Symbol

Parameter

Rating

Unit

VIN

Supply Voltage

-0.3 to 20

V

VSW

Switch Node Voltage

-1.0 to VIN +0.3

V

VBS

Bootstrap Voltage

VSW -0.3 to VSW +6.0

V

VFB

Feedback Voltage

-0.3V to +6.0

V

VEN

Enable/UVLO Voltage

-0.3V to +6.0

V

TST

Storage Temperature

-65 to +150

°C

TJ

Junction Temperature

+160

°C

TL

Lead Temperature

+260

°C

ESD Susceptibility (Note 5)

HBM

Human Body Model

2.5

kV

CDM

Charged Device Model

2

kV

Notes: 4. Stresses greater than the 'Absolute Maximum Ratings' specified above may cause permanent damage to the device. These are stress ratings only;

functional operation of the device at these or any other conditions exceeding those indicated in this specification is not implied. Device reliability may

be affected by exposure to absolute maximum rating conditions for extended periods of time.

5. Semiconductor devices are ESD sensitive and may be damaged by exposure to ESD events. Suitable ESD precautions should be taken when

handling and transporting these devices.

Thermal Resistance (Note 6)

Symbol

Parameter

Rating

Unit

θJA

Junction to Ambient

TSOT26

143

°C/W

θJC

Junction to Case

TSOT26

40

°C/W

Note: 6. Test condition for TSOT26: Device mounted on FR-4 substrate, single-layer PC board, 2oz copper, with minimum recommended pad layout

Recommended Operating Conditions (Note 7) (@TA = +25°C, unless otherwise specified.)

Symbol

Parameter

Min

Max

Unit

VIN

Supply Voltage

4.5

16

V

TA

Operating Ambient Temperature Range

-40

+85

°C

Note: 7. The device function is not guaranteed outside of the recommended operating conditions.

AP65101

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AP65101

Electrical Characteristics (@TA = +25°C, VIN = 12V, unless otherwise specified.)

Symbol

Parameter

Test Conditions

Min

Typ

Max

Unit

ISHDN

Shutdown Supply Current

VEN = 0V

-

-

1.0

µA

IQ

Supply Current (Quiescent)

VEN = 2.0V, VFB = 1.0V

-

0.83

-

mA

RDS(ON)1

High-Side Switch On-Resistance (Note 8)

-

-

200

-

mΩ

RDS(ON)2

Low-Side Switch On-Resistance (Note 8)

-

-

120

-

mΩ

ILIMIT

HS Current Limit

Minimum duty cycle

2

2.5

-

A

-

High-Side Switch Leakage Current

VEN = 0V, VSW =12V

-

-

1

μA

FSW

Oscillator Frequency

VFB = 0.75V

400

500

600

kHz

DMAX

Maximum Duty Cycle

VFB = 800mV

88

92

-

%

TON

Minimum On Time

-

-

90

-

ns

VFB

Feedback Voltage

TA = -40°C to +85°C

776

800

824

mV

VEN_RISING

EN Rising Threshold

-

1.4

1.5

1.6

V

VEN_FALLING

EN Falling Threshold

-

1.23

1.32

1.41

V

IEN

EN Input Current

VEN = 2V

-

2.85

-

μA

VEN = 0V

-

0

-

μA

INUVVTH

VIN Under Voltage Threshold Rising

-

3.7

4.05

4.4

V

INUVHYS

VIN Under Voltage Threshold Hysteresis

-

-

250

-

mV

TSS

Soft-Start Period

-

-

1

-

ms

TSHDN

Thermal Shutdown (Note 8)

-

-

+160

-

°C

THYS

Thermal Hysteresis (Note 8)

-

-

+20

-

°C

Note: 8. Guaranteed by design.

AP65101

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AP65101

Typical Performance Characteristics (@TA = +25°C, VIN = 12V, VOUT = 3.3V, L = 6.5µH, unless otherwise specified)

VIN=6.5V

VIN=12V

VIN=16V

VIN=4.7V

VIN=12V

VIN=16V

VIN=4.7V

VIN=12V

VIN=16V

VIN=4.7V

VIN=12V

VIN=16V

AP65101

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AP65101

Typical Performance Characteristics (@TA = +25°C, VIN = 12V, VOUT = 3.3V, L = 6.5µH, unless otherwise specified)

VIN=4.7V

VIN=12V

VIN=16V

VIN=4.7V

VIN=12V

VIN=16V

VIN=12V

VIN=16V

IOUT=1.5A

VIN=4.7V

IOUT=0A

IOUT=1A

AP65101

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AP65101

Typical Performance Characteristics (cont.)

(@TA = +25°C, VIN = 12V, VOUT = 3.3V, L = 6.5µH, C1 = 22µF, C2 = 22µF, unless otherwise specified.)

Startup Through VEN 1.5A Load

Time-1ms/div

Startup Through VIN 1.5A Load

Time-1ms/div

Short Circuit Test

Time-5ms/div

Shutdown Through VEN 1.5A Load

Time-50µs/div

Shutdown Through VIN 1.5A Load

Time-1ms/div

Short Circuit Recovery

Time-5ms/div

Startup Through VEN 0A Load

Time-1ms/div

Startup Through VIN 0A Load

Time-1ms/div

Transient Response (0.75 to 1.5A)

Time-100µs/div

Shutdown Through VEN 0A Load

Time-500ms/div

Shutdown Through VIN 0A Load

Time-500ms/div

Input/Output Ripple (IO=1.5A)

Time-2µs/div

VIN (12V/DIV)

VOUT (3.3V/DIV)

IOUT (1.5A/DIV)

SW (10V/DIV)

VEN (5V/DIV)

IOUT (1.5A/DIV)

SW (10V/DIV)

VOUT (3.3V/DIV)

VEN (5V/DIV)

VOUT (3.3V/DIV)

IOUT (1.5A/DIV)

SW (10V/DIV)

VIN (12V/DIV)

VOUT (3.3V/DIV)

IOUT (1.5A/DIV)

SW (10V/DIV)

VOUT (2V/DIV)

IOUT (2A/DIV)

VOUT (2V/DIV)

IOUT (2A/DIV)

IOUT (1A/DIV)

VOUT_AC (200mV/DIV)

VOUT_AC (100mV/DIV)

SW (10V/DIV)

VEN (5V/DIV)

IOUT (100mA/DIV)

SW (10V/DIV)

VOUT (3.3V/DIV)

VEN (5V/DIV)

VOUT (3.3V/DIV)

IOUT (100mA/DIV)

SW (10V/DIV)

VIN (12V/DIV)

VOUT (3.3V/DIV)

IOUT (100mA/DIV)

SW (10V/DIV)

VIN (12V/DIV)

VOUT (3.3V/DIV)

IOUT (100mA/DIV)

SW (10V/DIV)

IL (1.5A/DIV)

VIN_AC (200mV/DIV)

AP65101

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AP65101

Application Information

Theory of Operation

The AP65101 is a 1.5A current mode control, synchronous buck regulator with built in power MOSFETs. Current mode control assures excellent

line and load regulation and a wide loop bandwidth for fast response to load transients. The Figure 1 depicts the functional block diagram of

AP65101.

The operation of one switching cycle can be explained as follows. The rising edge of the 500kHz oscillator clock signal sets the RS Flip-Flop. Its

output turns on HS MOSFET. When the HS MOSFET is on, inductor current starts to increase. The current sense amplifier senses and amplifies

the inductor current. Since the current mode control is subject to sub-harmonic oscillations that start at half the switching frequency, ramp slope

compensation is utilized. This will help to stabilize the power supply. This ramp compensation is summed to the current sense amplifier output

and compared to the error amplifier output by the PWM comparator. When the sum of the current sense amplifier output and the slope

compensation signal exceeds the EA output voltage, the RS Flip-Flop is reset and HS MOSFET is turned off.

When the HS MOSFET turns off, the synchronous LS MOSFET turns on until the next clock cycle begins. There is a “dead time” between the HS

turn-off and LS turn-on that prevents the switches from “shooting through” from the input supply to ground.

For one whole cycle, if the sum of the current sense amplifier output and the slope compensation signal does not exceed the EA output, then the

falling edge of the oscillator clock resets the Flip-Flop, and forces the MOSFET to turn off.

The voltage loop is compensated internally.

Enable

The enable (EN) input allows the user to control turning on or off the regulator. The AP65101 has an internal pull-down resistor on the EN pin

and when the EN is not actively pulled up the part turns off.

Quiescent Current

Above the ‘EN Rising Threshold’, the internal regulator is turned on and the quiescent current can be measured above this threshold.

Automated No-Load and Light-Load Operation

The AP65101 operates in light load high-efficiency mode during low-load current operation. The advantage of this light-load efficiency mode is

lower power losses at no-load and light-load conditions. The AP65101 automatically detects the peak inductor current and enters the light load

high-efficiency mode when the inductor peak current goes below 500mA. Once the inductor peak current exceeds this level, the AP65101

transitions from light load high-efficiency mode to continuous PWM mode.

AP65101

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AP65101

Application Information (continued)

Current Limit and Hiccup Protection

In order to reduce the total power dissipation and to protect the application, AP65101 has cycle-by-cycle current-limiting implementation. The

voltage drop across the internal high-side MOSFET is sensed and compared with the internally set current-limit threshold. This voltage drop is

sensed at about 30ns after the HS turns on. When the peak inductor current exceeds the set current limit threshold, current limit protection is

activated. When the voltage at the FB pin reaches 0.2V the device enters Hiccup mode to periodically restart the part. This protection mode

greatly reduces the power dissipated on chip and reduces the thermal issue to protect the device. AP65101 will exit Hiccup mode when the over

current situation is resolved.

Undervoltage Lockout (UVLO)

Undervoltage Lockout is implemented to prevent the IC from insufficient input voltages. The AP65101 has a UVLO comparator that monitors the

input voltage and the internal bandgap reference. If the input voltage falls below 4.4V, the AP65101 will latch the undervoltage fault. In this event,

the output will be pulled low and power has to be re-cycled to reset the UVLO fault.

Overvoltage Protection

When the AP65101 FB pin exceeds 115% of the nominal regulation voltage of 0.8V, the overvoltage comparator is tripped.

Thermal Shutdown

The AP65101 has on-chip thermal protection that prevents damage to the IC when the die temperature exceeds safe margins. It implements a

thermal sensing to monitor the operating junction temperature of the IC. Once the die temperature rises to approximately +160°C, the thermal

protection feature gets activated. The internal thermal sense circuitry turns the IC off thus preventing the power switch from damage.

A hysteresis in the thermal sense circuit allows the device to cool down to approximately +120°C before the IC is enabled again through soft

start. This thermal hysteresis feature prevents undesirable oscillations of the thermal protection circuit.

Setting the Output Voltage

The output voltage can be adjusted using an external resistor divider. Table 1 shows a list of resistor selection for common output voltages.

Resistor R1 is selected based on a design tradeoff between efficiency and output voltage accuracy. For high values of R1 there is less current

consumption in the feedback network. R1 can be determined by the following equation:











 1

0.8

V

RR OUT

21

Vout

FB

R1

R2

RT

Figure 2. Feedback Divider Network

Table 1. Recommended Component Selection

VOUT (V)

R1 (kΩ)

R2 (kΩ)

RT (kΩ)

L1 (µH)

1.05

10

32.4

150

2.2

1.2

20.5

41.2

130

2.2

1.8

40.2

32.4

100

3.3

2.5

40.2

19.1

59

4.7

3.3

40.2

13

59

6.5

5

40.2

7.68

59

6.5

AP65101

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AP65101

Application Information (cont.)

Inductor

Calculating the inductor value is a critical factor in designing a buck converter. For most designs, the following equation can be used to calculate

the inductor value;

SWLIN

OUTINOUT

fΔIV

)V(VV

L





Where

L

ΔI

is the inductor ripple current and

SW

f

is the buck converter switching frequency.

Choose the inductor ripple current to be 30% of the maximum load current. The maximum inductor peak current is calculated from:

2

ΔI

II L

LOADL(MAX) 

Peak current determines the required saturation current rating, which influences the size of the inductor. Saturating the inductor decreases the

converter efficiency while increasing the temperatures of the inductor and the internal MOSFETs. Hence choosing an inductor with appropriate

saturation current rating is important.

A 1µH to 10µH inductor with a DC current rating of at least 25% higher than the maximum load current is recommended for most applications.

For highest efficiency, the inductor’s DC resistance should be less than 20mΩ. Use a larger inductance for improved efficiency under light load

conditions.

Input Capacitor

The input capacitor reduces the surge current drawn from the input supply and the switching noise from the device. The input capacitor has to

sustain the ripple current produced during the on time on the upper MOSFET. It must hence have a low ESR to minimize the losses.

The RMS current rating of the input capacitor is a critical parameter that must be higher than the RMS input current. As a rule of thumb, select an

input capacitor which has RMs rating that is greater than half of the maximum load current.

Due to large dI/dt through the input capacitors, electrolytic or ceramics should be used. If a tantalum must be used, it must be surge protected.

Otherwise, capacitor failure could occur. For most applications, a 10/22µF ceramic capacitor is sufficient.

Output Capacitor

The output capacitor keeps the output voltage ripple small, ensures feedback loop stability and reduces the overshoot of the output voltage. The

output capacitor is a basic component for the fast response of the power supply. In fact, during load transient, for the first few microseconds it

supplies the current to the load. The converter recognizes the load transient and sets the duty cycle to maximum, but the current slope is limited

by the inductor value.

Maximum capacitance required can be calculated from the following equation:

ESR of the output capacitor dominates the output voltage ripple. The amount of ripple can be calculated from the equation below:

ESR*ΔIVout inductorcapacitor 

An output capacitor with ample capacitance and low ESR is the best option. For most applications, a 22µF ceramic capacitor will be sufficient.

2

out

2

out

2

inductor

out

oV)V V(Δ

)

2

ΔI

L(I

C





Where

ΔV

is the maximum output voltage overshoot.

AP65101

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AP65101

Application Information (cont.)

PC Board Layout

This is a high-switching frequency converter. Hence attention must be paid to the switching currents interference in the layout. Switching current

from one power device to another can generate voltage transients across the impedances of the interconnecting bond wires and circuit traces.

These interconnecting impedances should be minimized by using wide, short printed circuit traces.

Figure 3—PC Board Layout

External Bootstrap Diode

It is recommended that an external bootstrap diode be added when the input voltage is no greater than 5V or the 5V rail is available in the

system. This helps to improve the efficiency of the regulator. This solution is also applicable for D > 65%. The bootstrap diode can be a low cost

one such as BAT54 or a Schottky that has a low VF.

AP65101

BST

SW

10nF

BOOST

DIODE

5V

Figure 4—External Bootstrap Compensation Components

Recommended Diodes:

Part Number

Voltage/Current

Rating

Vendor

B130

30V, 1A

Diodes Inc

SK13

30V, 1A

Diodes Inc

AP65101

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AP65101

Ordering Information

AP65101WU - 7

Packing

Package

WU : TSOT26 7 : Tape & Reel

Part Number

Package Code

Package

Identification Code

Tape and Reel

Quantity

Part Number Suffix

AP65101WU-7

WU

TSOT26

RA

3,000

-7

Marking Information

(1) TSOT26

1 2 3

6

7

4

XX YW X

XX : Identification Code

Y : Year 0~9

X : A~Z : Green

( Top View )

5

W : Week : A~Z : 1~26 week;

a~z : 27~52 week; z represents

52 and 53 week

Part Number

Package

Identification Code

AP65101WU-7

TSOT26

RA

AP65101

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AP65101

Package Outline Dimensions (All dimensions in mm.)

Please see AP02002 at http://www.diodes.com/datasheets/ap02002.pdf for the latest version.

(1) TSOT26

Suggested Pad Layout

Please see AP02001 at http://www.diodes.com/datasheets/ap02001.pdf for the latest version.

(1) TSOT26

TSOT26

Dim

Min

Max

Typ

A



1.00



A1

0.01

0.10



A2

0.84

0.90



D





2.90

E





2.80

E1





1.60

b

0.30

0.45



c

0.12

0.20



e





0.95

e1





1.90

L

0.30

0.50

L2





0.25

θ

0°

8°

4°

θ1

4°

12°



All Dimensions in mm

Dimensions

Value (in mm)

C

0.950

X

0.700

Y

1.000

Y1

3.199

c

A1

L

E1 E

A2

D

e1

e

6x b



4x 1 

L2

A

Y1

C C

X (6x)

Y (6x)

AP65101

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AP65101

IMPORTANT NOTICE

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INCLUDING, BUT NOT LIMITED TO, THE IMPLIED WARRANTIES OF MERCHANTABILITY AND FITNESS FOR A PARTICULAR PURPOSE

(AND THEIR EQUIVALENTS UNDER THE LAWS OF ANY JURISDICTION).

Diodes Incorporated and its subsidiaries reserve the right to make modifications, enhancements, improvements, corrections or other changes

without further notice to this document and any product described herein. Diodes Incorporated does not assume any liability arising out of the

application or use of this document or any product described herein; neither does Diodes Incorporated convey any license under its patent or

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Diodes Incorporated does not warrant or accept any liability whatsoever in respect of any products purchased through unauthorized sales channel.

Should Customers purchase or use Diodes Incorporated products for any unintended or unauthorized application, Customers shall indemnify and

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final and determinative format released by Diodes Incorporated.

LIFE SUPPORT

Diodes Incorporated products are specifically not authorized for use as critical components in life support devices or systems without the express

written approval of the Chief Executive Officer of Diodes Incorporated. As used herein:

A. Life support devices or systems are devices or systems which:

1. are intended to implant into the body, or

2. support or sustain life and whose failure to perform when properly used in accordance with instructions for use provided in the

labeling can be reasonably expected to result in significant injury to the user.

B. A critical component is any component in a life support device or system whose failure to perform can be reasonably expected to cause the

failure of the life support device or to affect its safety or effectiveness.

Customers represent that they have all necessary expertise in the safety and regulatory ramifications of their life support devices or systems, and

acknowledge and agree that they are solely responsible for all legal, regulatory and safety-related requirements concerning their products and any

use of Diodes Incorporated products in such safety-critical, life support devices or systems, notwithstanding any devices- or systems-related

information or support that may be provided by Diodes Incorporated. Further, Customers must fully indemnify Diodes Incorporated and its

representatives against any damages arising out of the use of Diodes Incorporated products in such safety-critical, life support devices or systems.

Copyright © 2015, Diodes Incorporated

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