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CDBC455CX3(CDBC455C3) The Piezoelectric Effect
Piezoelectric Effect Basics
A piezoelectric substance is one that produces an electric charge when a mechanical stress is applied (the substance is squeezed or stretched). Conversely, a mechanical deformation (the substance shrinks or expands) is produced when an electric field is applied. This effect is formed in crystals that have no center of symmetry. To explain this, we have to look at the individual molecules that make up the crystal. Each molecule has a polarization, one end is more negatively charged and the other end is positively charged, and is called a dipole. This is a result of the atoms that make up the molecule and the way the molecules are shaped. The polar axis is an imaginary line that runs through the center of both charges on the molecule. In a monocrystal the polar axes of all of the dipoles lie in one direction. The crystal is said to be symmetrical because if you were to cut the crystal at any point, the resultant polar axes of the two pieces would lie in the same direction as the original. In a polycrystal, there are different regions within the material that have a different polar axis. It is asymmetrical because there is no point at which the crystal could be cut that would leave the two remaining pieces with the same resultant polar axis. Figure 1 illustrates this concept.
Monocrystal with single polar axis
Polycrystal with random polar axis
Figure 1: Mono vs. Poly Crystals
In order to produce the piezoelectric effect, the polycrystal is heated under the application of a strong electric field. The heat allows the molecules to move more freely and the electric field forces all of the dipoles in the crystal to line up and face in nearly the same direction (Figure 2).
Electrode
Random Dipole
Polarization
Surviving Polarity
Figure 2: Polarization of Ceramic Material to Generate Piezoelectric Effect
The piezoelectric effect can now be observed in the crystal. Figure 3 illustrates the piezoelectric effect. Figure 3a shows the piezoelectric material without a stress or charge. If the material is compressed, then a voltage of the same polarity as the poling voltage will appear between the electrodes (b). If stretched, a voltage of opposite polarity will appear (c). Conversely, if a voltage is applied the material will deform. A voltage with the opposite polarity as the poling voltage will cause the material to expand, (d), and a voltage with the same polarity will cause the material to com-
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press (e). If an AC signal is applied then the material will vibrate at the same frequency as the signal (f).
-
+
Poling -
Axis +
(a) +
+-
+ (b)
-
-
+
-
(c)
-
+-
+
(d) -
+ (e)
(f)
Figure 3: Example of Piezoelectric Effect
Using the Piezoelectric Effect
The piezoelectric crystal bends in different ways at different frequencies. This bending is called the vibration mode. The crystal can be made into various shapes to achieve different vibration modes. To realize small, cost effective, and high performance products, several modes have been developed to operate over several frequency ranges. These modes allow us to make products working in the low kHz range up to the MHz range. Figure 4 shows the vibration modes and the frequencies over which they can work.
An important group of piezoelectric materials are ceramics. Murata utilizes these various vibration modes and ceramics to make many useful products, such as ceramic resonators, ceramic bandpass filters, ceramic discriminators, ceramic traps, SAW filters, and buzzers.
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PZT Application Manual
Vibration Mode
Flexure Vibration
Frequency (Hz) 1K 10K 100K 1M 10M 100M 1G
Application Piezo Buzzer
Lengthwise Vibration
KHz Filter
Area Vibration
KHz Resonator
Radius Vibration
Thickness Shear Vibration
Thickness Trapped Vibration
Surface Acoustic Wave
BGS Wave
MHz Filter
MHz Resonator
SAW Filter SAW Resonator SH Trap SH Resonator SH Filter
Figure 4: Various Vibration Modes Possible with Piezoelectric Ceramics
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Piezoelectric Resonators
Introduction
Ceramic resonators are piezoelectric ceramic devices that are designed to oscillate at certain frequencies. They are highly stable, small, inexpensive, and do not require tuning or adjusting. Other common resonant devices are quartz crystal and discrete LC/ RC resonators. Although ceramic resonators do not have as good a total oscillation frequency tolerance as quartz crystal resonators, they are much more frequency tolerant than LC or RC circuits, and smaller and cheaper than quartz. Resonators are typically used with the clock circuitry found built-in to most microcontrollers to provide timing for the microcontrollers. The resonators by themselves cannot be clocks, because they are passive components (components that consume electrical energy). In order for a resonator to oscillate, an active component (a component that produces electrical energy) is needed. This active component is typically included in microcontrollers and is usually referred to as the clock circuit. There are prepackaged stand-alone oscillator circuits that have both the active and passive parts in one package. To explain, a discussion of oscillation principles is needed.
Principles of Oscillation
There are two main types of oscillating circuit, Colpitts and Hartley. These circuits are shown in Figure 5.
Colpitts Oscillator
Hartley Oscillator
Figure 5: Colpitts and Hartley Oscillator
The Colpitts circuit is normally used (over the Hartley circuit) because it is cheaper and easier to have two capacitors and one inductor rather than two inductors and one capacitor. These circuits oscillate because the output is fed back to the input of the amplifier. Oscillation occurs when the following conditions are met (Barkhausen Criterion for oscillation): loop gain ( x ) 1 and phase = 1 + 2 = 360o x n (n = 1, 2, 3, ...). Figure 6 illustrates the idea of feedback oscillation.
Amplifier Gain: Phase Shift: 1
Feedback Network Transfer Function:
Phase Shift: 2
Figure 6: Block Diagram of Oscillator
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PZT Application Manual
Gain/Phase Conditions vs. Barkhausen Criterion
It is possible to look at the true gain and phase response of an oscillation circuit. This is different from the loop gain we refer to when talking about Barkhausen criterion. True gain / phase measurement is done by breaking open the oscillation circuit and measuring the gain and phase response of the circuit using a gain/phase analyzer or a signal generator with a vector voltmeter. Such measurement can provide a very accurate picture as to whether or not the oscillation circuit will actually oscillate. As an example of the measured gain/phase results, the circuit gain/phase response shown in Figure 7a can oscillate because it has a gain greater than 0dB at the zero crossing point of the phase. The circuit gain/phase response in Figure 7b will not oscillate because the gain is less than 0dB when the phase crosses zero. A gain greater than 0dB is needed when the phase crosses the 0 degree axis in order for oscillation to occur.
LoopGain (dB) Phase (deg)
LoopGain (dB) Phase (deg)
a) Possible To Oscillate
b) Impossible To Oscillate
40
40
30
Phase
20
90
10
30
20
90
Phase 10
0
0
0
0
-10
-10 Gain
-20
-90
-20
-30
Gain
-90
-30
-40 3.90
4.00
4.10
Frequency (MHz)
-40 3.90
4.00
4.10
Frequency (MHz)
Figure 7: Gain - Phase Plots for Possible and Impossible Oscillation
The circuit in Figure 8 is the circuit used for these gain phase measurements. The oscillation circuit is broken open and
a signal generator applies a range of frequencies to the inverter (amplifier). At the output of the circuit (after the resona-
tor / feedback network), a vector voltmeter is used to measure gain and phase response at each frequency.
As mentioned in the example above, the gain must be greater than 0dB where the phase crosses the zero degree axis.
Sometimes the loop gain of the Barkhausen criterion is confused for this gain condition (greater than 0dB). In the previous section, it was mentioned that for Barkhausen criterion to be met, loop gain ( x ) must be greater than or equal to one (( x ) 1). This may sound like a contradiction when we mention that the gain/phase measurement must be at least 0dB for oscillation to occur. Why is one loop gain at 1 and the other at 0? The reason for this confusion is that Barkhausen x is a unitless quantity and not a decibel measurement (like the loop gain in a gain/phase measurement). Both conditions really say the same thing, but in two different ways. The expression for calculating loop gain (in decibels) is 10log(V2/V1), where V2 is output voltage and V1 is input voltage. and are actually gain multiplying factors and are unitless. Since the oscillation circuit is broken open, as shown in Figure 8, the voltage from the frequency generator is passed through the amplifier (multiplied by ), passed through the feedback network (multiplied by ), and passed through the vector voltmeter. From this, you can use the following expression to show what V2 is in terms of V1, , and : V2=V1 x x . This can be re-written into this form: V2/V1= x , and substituted in to the decibel loop gain equation: Gain (dB) = 10log( x ). This equation is a key point. From Barkhausen criterion, x must be 1 for oscillation to occur. If 1 is substituted into the new equation: dB = 10log(1), the dB calculation will equal 0dB. For oscillation to occur Barkhausen criterion must be meet ( x ) 1, which is the same as saying the loop gain measurement must be 0 dB (at the zero crossing of the phase).
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.
Amplifier , 1 IC
0.01µF
Zo = 50
Rf
~ Vin
Feedback Network , 2
CL2
CL1
2pF
Vector Voltmeter 10M
How Does It Work
Figure 8: Gain - Phase Test Circuit
Why Resonators
The most common use of a resonator, ceramic or quartz crystal, is to take advantage of the fact that the resonator becomes inductive between the resonant and anti-resonant frequencies (see Figure 9), which allows replacement of the inductor in the Colpitts circuit.
Ceramic Resonator Basics
A ceramic resonator utilizes the mechanical vibration of the piezoelectric material. Figure 9 shows the impedance and phase characteristics of a ceramic resonator. This plot of impedance and phase is made using a network analyzer, sweeping the resonator around it's oscillation frequency. The graphs show that the resonator becomes inductive between the resonant frequency, fr, and the anti-resonant frequency, fa. This means that the resonator can resonate (or the oscillator using the resonator can oscillate) between these two frequencies. Figure 9 also shows that the minimum impedance for the resonator occurs at fr (called the resonant impedance) and the maximum impedance occurs at fa (called the anti-resonant impedance). At most other frequencies, the resonator is capacitive, but there are other frequencies at which the part is inductive (referred to as overtones). Since the resonator appears to be an inductor (with some small series resistance) at the resonant frequency, we can use this part to replace the inductor shown in the Colpitts oscillator in Figure 5. You will want to replace the inductor with a resonator that resonates at the desired frequency.
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Impedance|Z| ()
fa fr
+90
Phase (deg)
0
C
L
C
-90
Frequency Figure 9: Resonator Impedance and Phase Plot
The Resonator Circuit Model
Looking at the resonator's characteristics we see an equivalent circuit for the resonator consisting of a capacitor (C1), inductor (L1), and resistor (R1) in series and a capacitor (Co) in parallel (Figure 10).
C1
L1
R1
Co
Figure 10: Equivalent Circuit Model for Two Terminal Ceramic Resonator
If the equivalent circuit values are known, then we can use this circuit to calculate the values of fr, fa, F and Qm using the following equations:
fr =
1
2 L1C1
fa = 2
1 L1C1Co Co + C1
F = fa - fr
Qm = 1 2frC1R1
Equation 1: Equations for Calculating Resonator Parameter based on Equivalent Circuit Model
F is the difference between the resonant and anti-resonant frequencies.
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Qm is the mechanical Q of the resonator.
Appendix 1 gives the equivalent circuit values of some common resonators. Between the resonant and anti-resonant frequencies (where is possible for the resonator to resonate in an oscillation circuit) the equivalent circuit simplifies to an inductor and resistor in a series connection. This is why the resonator can be used to replace the inductor in the Colpitts circuit. The resonator can be designed to work over different frequency ranges by changing the shape of the ceramic element and the vibration mode.
Overtones of the Resonator
The ceramic resonator will oscillate at a fundamental frequency (between fr and fa) but can also be made to oscillate at odd overtones of the fundamental frequency. This odd overtone oscillation can be done intentionally (as in the case of third overtone resonators to be discussed later) or as a result of a poorly designed oscillation circuit. These overtones occur naturally in resonators and have impedance and phase responses similar to the fundamental except that they are smaller and occur at odd multiples of the fundamental frequency (Figure 11). Even overtone oscillation is not possible with ceramic resonators.
Fundamental
3rd 5th
7th
9th
Impedance
Frequency
Figure 11: Ceramic Resonator Impedance Response Plot Showing Odd Overtones
In the figure, you can see the fundamental frequency and the 3rd, 5th, 7th, etc. overtones. When power is applied to the oscillation circuit, the oscillation begins as high frequency noise and drops in frequency (moves from right to left in Figure 11) until it reaches a point that meets the stable oscillation criteria (Barkhausen Criterion) discussed earlier. In a well designed circuit, this point will be at the fundamental response or an intentionally desired third overtone response. When designing lower frequency resonators (below~13MHz), we design the resonator to have the intended oscillation frequency occur at the fundamental. For higher frequency parts (above ~13MHz), we actually use the 3rd overtone response. To achieve operating frequencies above 12~13MHz, it is most efficient to use the 3rd overtone, instead of trying to design a fundamental mode resonator for these frequencies. Since we are dealing with ceramic material, a combination of various raw materials which are mixed together and then fired, we do not have to live with the weakness of quartz crystal based resonators, when used in 3rd overtone operation. Quartz crystals use a grown crystal material, which does not allow for material changes. To allow a quartz resonator to operate at the 3rd overtone, the fundamental response of the quartz resonator must be suppressed, typically by an external tank circuit. Use of an external tank circuit adds to the cost and complexity of oscillator design. For ceramic resonators, using the aeolotropic ceramic material (different from standard ceramic material), the fundamental frequencies are naturally suppressed, without the need of an external tank circuit, and the 3rd harmonics can be easily used for oscillation (Figure 12). This use of aeolotropic material allows for the efficient and cost effective manufacture of higher frequency resonators.
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PZT Application Manual
Impedance
Since the 3rd overtone is three times the fundamental frequency, using 3rd overtone can extend the frequency range covered by ceramic resonators considerably (up to 60MHz). Ceramic resonators, unlike quartz crystal resonators, do not require an external tank circuit for 3rd overtone operation, due to the aeolotropic ceramic material.
3rd Fundamental
5th
Frequency Figure 12: Impedance Response of Third Overtone Based Ceramic Resonator As shown in Figure 12, the fundamental response of the ceramic resonator is suppressed to the point that the 3rd overtone appears to be the main ("fundamental") response of the oscillation circuit. Please note that greater care must be taken in designing the oscillation circuit, since it is easier to have suppressed fundamental or 5th overtone spurious oscillations (compared to fundamental resonator's spurious oscillations at 3rd or 5th overtone).
Vibration Modes
Ceramic resonators can employ one of several possible vibration modes, depending on the desired oscillation frequency. The vibration mode used is dictated by the target frequency of the resonator. The vibration mode selected dictates the basic shape of the resonator. In the following, each vibration mode used commonly for ceramic resonators and the range of oscillation frequencies possible are explained in more detail.
· Area Vibration (375kHz to 1250kHz) The kHz range resonators utilize area vibration in their operation (Figure 13). In this mode, the center of the substrate is anchored while the corners of the material expand outward. This vibration mode suffers from spurious oscillation due to thickness vibration, but core circuit design can easily suppress such spurious oscillation. The resonant frequency is determined by the length of the square substrate. This mode operates from about 375kHz to 1250kHz.
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Electrode
L
Area Vibration Figure 13: Ceramic Element for Area Vibration · Thickness Shear Vibration (1.8MHz to 6.3MHz) The MHz range resonators use two vibration modes. The first MHz range vibration mode is thickness shear vibration (Figure 14). In this mode, the substrate expands in thickness as well as diagonally. The resonant frequency is determined by the thickness of the substrate. This mode works from 1.8MHz to 6.3MHz.
t
Thickness Shear Vibration
Figure 14: Ceramic Element for Thickness Shear Vibration · Thickness Longitudinal Vibration (6.3MHz to 13.0MHz)
The second MHz range vibration mode is thickness longitudinal vibration (Figure 15). In this mode, the substrate thickness expands and contracts. The resonant frequency is determined by the thickness of the substrate. This mode
operates from 6.3MHz to 13.0MHz. Using 3rd overtone this range can be extended to cover 12MHz to 60MHz.
t
Thickness Vibration
Figure 15: Ceramic Element for Thickness Longitudinal Vibration
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PZT Application Manual
· Thickness Longitudinal Vibration, Third Overtone (13.0MHz to 60.0MHz) By taking the thickness longitudinal vibration mode mentioned above and changing the ceramic material to an aeolotropic ceramic material, the fundamental response of the thickness longitudinal vibration mode is suppressed allowing use of the third overtone. Figure 15 still represents this vibration mode, except that aeolotropic ceramic material is used. By using this third overtone of the thickness longitudinal vibration mode, it is possible to make ceramic resonators up to 60MHz.
Resonator Configurations
Resonators can come in two different configurations. A resonator can be supplied in a two terminal package (leaded or SMD) or in a three terminal package (leaded or SMD). For the two terminal package (Murata part numbers with the CSA prefix), the ceramic resonator element is connected between the two terminals. For the three terminal package (Murata part numbers with the CST prefix), there is an additional terminal between the two terminals of the two terminal type resonator. This third or middle terminal is a ground terminal for the built-in load capacitors. Recall from Figure 5 where the Colpitts oscillator is shown, there is a single inductor and two capacitors. The inductor would be replaced by the ceramic resonator, but the external capacitors (called load capacitors) must still be added. The three terminal resonator offers the convenience of having these two load capacitors built-in to the resonator, where this middle terminal is the ground for the load caps. The load capacitors that Murata builds into the resonator also provide some benefit in offsetting shifts in oscillation frequency due to temperature effects. Figure 16 shows the common lower frequency resonator packages for two and three terminal resonators. .
Two Terminal Leaded
Three Terminal Leaded
Two Terminal SMD
Three Terminal SMD
Figure 16: Two and Three Terminal Resonator
Spurious Oscillations
The odd overtones (3rd, 5th, etc. for fundamental mode resonators, or suppressed fundamental, 5th, etc. for third overtone resonators) are always present as spurious oscillations. Also, other vibration modes can cause spurious oscillation. These other vibration modes are the same ones employed to make higher frequency resonators. These can be suppressed by properly designing the hookup circuit around the resonator. Care must be taken in determining oscillator hook-up circuit to insure desired operation. Without a correctly designed oscillation circuit, undesired spurious oscillation can occur. Resonators are designed to use one vibration mode but suffer from spurious oscillation due to other vibration modes. These can be controlled to a certain extent by using the correct value of load capacitors or dampening resistor (Rd) to suppress gain at the overtone's frequency. One of the most common spurious oscillations for kHz range resonators is a result of an undesired vibration mode, thickness vibration. This causes a hump in the frequency response around 4
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5 MHz (Figure 17).
Thickness Vibration
Impedance
0
5M
10M
Frequency (Hz)
Figure 17: Impedance Response Plot of kHz Resonator Showing Thickness Vibration Spurious Response
Resonator Specifications
Nominal Oscillation Frequency This is the oscillation frequency of the resonator measured in a specified test circuit.
Frequency Tolerance
There are three types of frequency tolerance (Initial, Temperature, and Aging) that go into the complete tolerance specification for a ceramic resonator. These tolerances are provided as a +/- percentage and are listed individually on a resonator's specification. These tolerances are all added to make the complete tolerance specification.
· Initial tolerance This is how much the frequency will vary based on slight differences in materials, production methods, and other factors, at room temperature. This tolerance results from the fact that every part cannot be exactly the same. There will always be some small difference from one part to another.
· Temperature tolerance This is a measure of how much the frequency varies with a change in temperature. Ceramic materials have a positive temperature coefficient. This means that as the temperature increases the resonator frequency increases. For the resonators that have built in load capacitors, since the capacitors are made of a ceramic material similar to the resonator ceramic, the value of the load capacitors increases with temperature. However, increasing the value of the load capacitors decreases the oscillation frequency, which helps to compensate for the increase of resonator frequency. For this reason, the resonators with built in load capacitors will have better temperature tolerance specifications than resonators without built-in load caps.
· Aging tolerance This is a measure of how much the frequency will vary over the life of the part (typically 10 years).
Built In Capacitance Values
Indicates the built-in load capacitor value inside of the resonator and the tolerance of this capacitor's values. This only applies to resonators where there part numbers start with the "CST" (like: CST..., CSTS..., CSTCV..., etc.)
Resonant Impedance
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PZT Application Manual
This is a specification of the impedance occurring at fr. Lower values for resonant impedance are desired. The lower the resonant impedance is in a given resonator, then less gain is required in the oscillation circuit for oscillation to start and continue. The specification usually list a maximum value of impedance that will not be exceeded by any resonator made to this specification.
Insulation Resistance This is the measurement of resistance between the two terminals of the resonator at some given DC voltage. At DC, the resonator should appear capacitive and have a high resistance between the terminals. Remember, the part only achieves low impedance near its oscillation frequency, not DC.
Withstanding Voltage Indicates the maximum DC voltage that may be applied across the outside terminals (not including ground terminal of CST type resonators) for a given time.
Absolute Maximum Voltage · Maximum D.C. Voltage Indicates the maximum DC voltage that can be applied to the resonator continuously. · Maximum Input Voltage Indicates the maximum AC peak to peak voltage that may be applied to the resonator.
Operational Temperature Range Murata offers ceramic resonators in two different temperature ranges: Standard and Automotive.
· Standard (-20C to +80C) Standard temperature range resonators will remain in specification over the temperature range of -20C to +80C. Exceeding this range can cause the resonator to perform outside of specification. · Automotive (-40C to +125C) Automotive grade resonators are exactly the same as standard resonators, except all automotive grade parts go through additional sorting to insure performance over the wider temperature range and in an automotive environment. These sorted resonators are also capable of passing the rigorous thermal cycling requirements of automotive customers. Automotive is a bit of a misnomer since automotive grade parts are not only for automotive applications, but for any application that requires an extended temperature range.
Storage Temperature range This temperature range indicates the temperature at which the resonator can be safely stored in a non-operating condition. This range will vary depending on whether the resonator has a standard or an automotive temperature rating.
Test Circuit The test circuit indicates the circuit used to test the resonator for compliance with specification. The ceramic resonator is sorted for 100% spec compliance in production, using this test circuit.
Comparison of Crystal and Ceramic Resonators
In the previous sections, the basic operation of a ceramic resonator has been discussed and some comparisons made to quartz crystal resonators. At this point, we should look at the differences between these two types of resonators. There are several advantages that ceramic resonators have over quartz crystal resonators. Figure 18 shows the characteristics of ceramic and quartz crystal resonators. As can be seen, the quartz crystal has a much tighter frequency tolerance, as indicated by a smaller difference between fa and fr. This tighter frequency tolerance is the major advantage of quartz crystal based resonators over ceramic based resonators.
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Ceramic Resonator
Impedance Impedance
Quartz Crystal Resonator
Frequency
Frequency
Figure 18: Impedance Response Comparison between Ceramic and Quartz Resonators
Table 1 shows a comparison of the electrical characteristics between ceramic resonators and quartz crystal resonators (BOLD = better, where appropriate).
Ceramic Resonator
Quartz Crystal
Frequency Tolerance
±0.2 ~ ±0.5%
±0.005%
Temperature Characteristics
20 ~ 50 ppm/oC
0.5 ppm/oC
Static Capacitance
10 ~ 50pF
10pF max.
Qm
102 103
104 105
F
0.05 X Fosc
0.002 X Fosc
Rise Time
10-5 10-4 Sec
10-3 - 10-2 Sec
Height (leaded)
7.5mm (Typ)
13.5mm (Typ)
Price Index
1
2
Table 1. Basic Resonator Parameter Comparison Between Ceramic and Quartz Resonator
As can be seen from the table, quartz crystal resonators have a much better frequency tolerance than ceramic resonators. They have a higher mechanical Q and a smaller F. For tight frequency tolerance applications, quartz crystal resonators are the choice. Ceramic resonators have a much faster rise time, smaller size, and are about half the price. In addition, ceramic resonators have a better mechanical shock and vibration resistance. They will not break as easily as quartz resonators. Drive level, a big issue with quartz crystal resonators, is not an issue with ceramic resonators. Most applications can accept the looser frequency tolerance of the ceramic resonator, while enjoying the other benefits. Quartz crystal resonators require a LC tank circuit in order to suppress the fundamental and work with 3rd overtones, where ceramic resonators do not. This saves in cost of parts for the circuit, storing the parts, space on the board, and time needed to place the parts in production.
Design Considerations
Hook Up Circuit
While Murata strongly recommends that all customers take advantage of Murata's characterization service (see Appendix 3 and some comments later in this section), the following will provide a basic explanation of the external hook-up circuit for a ceramic resonator and what effect each component in the hook up circuit has to oscillation.
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PZT Application Manual
Figure 19 shows a basic oscillation circuit using a CMOS inverter (you can use a HCMOS inverter for higher frequency oscillators). For oscillation circuits using inverters, it is not recommended to use buffered inverters. Unbuffered inverters are desired since they have less gain, which decreases the chance for spurious overtone oscillation.
INV. 1
INV. 2
Output
Rf Rd
X
CL1
CL2
Figure 19: Typical Hook-up Circuit for Ceramic Resonator
INV. 1 is simply an inverting amplifier and is the active component of the oscillation circuit. INV. 2 is used as a waveform sharper (makes the sinusoidal output of INV. 1 into a square wave) and a buffer for the output. It squares off the output signal and provides a clear digital signal.
· Rf Rf provides negative feedback around INV. 1 so that INV. 1 works in its linear region and allows oscillation to start once power is applied. If the feedback resistance is too large and if the insulation resistance of the inverter's input is decreased then oscillation will stop due to the loss of loop gain. If it is too small then the loop gain will be decreased and it will adversly effect the response of the fundumental and 3rd overtone response (could lead to 5th overtone oscillation). A Rf of 1 M is generally recommended for use with a ceramic resonator, regardless of resonator frequency.
· Rd The damping resistor, Rd has several effects. First, without Rd, the output of the inverter sees the low impedance of the resonator. This low impedance of the resonator causes the inverter to have a high current draw. By placing Rd at the output of the inverter, the output resistance is increased and the current draw is reduced. Second, it stabilizes the phase of the feedback circuit. Finally, and most importantly, it reduces loop gain at higher frequencies. This is very helpful when dealing with a high gain inverter / clock circuits. If the gain is too high, the chance for spurious oscillations is greatly increased at the resonator's overtones or other vibration modes (i.e. high frequencies). Rd works with CL2 to form a low pass filter, which minimally effects gain at the fundamental frequency, while greatly effecting gain at higher frequencies. This is one tool for removing unwanted overtone or spurious oscillations.
· Load Capacitors The load capacitors, CL1 and CL2, provide a phase lag of 180o as well as determine controlling frequency of oscillation. The load capacitor values depend on the application, the IC, and the resonator itself. If the values are too small, then the loop gain at all frequencies will be increased and could lead to spurious overtone oscillation. This is particularly likely around 4 5 MHz where the thickness vibration mode lies with kHz resonators. For MHz resonators, the spurious oscillation is likely to occur at the 3rd harmonic frequencies (even with 3rd overtone MHz resonators). If the resonator circuit is oscillating at a substantially higher frequency, then increasing the load capacitor may solve the problem. *Changes in load capacitance effect gain at all frequencies (unlike Rd). Increase load cap values to cut gain, decrease load cap values to boost gain, for all frequencies.
*Please Note: As mentioned above, the resonator itself can effect which load capacitor values should used in any given oscillation circuit. This is important to note, when comparing ceramic resonators, from various ceramic resonator
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manufacturers, in an oscillation circuit. Since the ceramic material used to make the resonator is a little different from manufacturer to manufacturer (thus the equivalent circuit of the resonator is slightly different), it is very common to see one manufacturer's resonator need certain load cap value in an oscillation circuit, but another manufacturer's resonator needs another load cap value for stable oscillation (in the same circuit). Also, the sorting IC (test circuit used in production) used to determine oscillation freqeuncy (to resonator specification) can also differ by resonator makers. Do not assume that if you get a supplier "A"'s resonator to work with a given load cap value, that supplier "B"'s resonator will need same load cap value. Also be aware that if load cap values / IC combination works at one freqeuncy, the load caps may need to be different for the same IC at other freqeuncies. By using Murata's free IC characterization service (later in this section or see Appendix 3), such problems and concerns can be completely avoided in your design.
· Test Circuit Types The circuit in Figure 19 is the standard test circuit used by Murata on all of our resonators. We use an unbuffered CMOS chip (RCA/Harris CD4069UBE), an unbuffered HCMOS (Toshiba TC40H004P) or an unbuffered HCMOS (Toshiba TC74HCU04) chip as a reference for all of the published specifications. The test circuit used is indicated on the data sheet for the part. CMOS is typically used with lower frequency resonators while HCMOS is used with the higher frequency resonators. The resonator part number calls out which type of CMOS inverter is used. Please see the section on resonator part numbering for clarification of this point. Appendix 2 gives the standard test circuit values for Murata's resonators
Irregular Oscillation
As mentioned in the section on "Spurious Oscillation", spurious oscillations can sometimes occur if the hook-up circuit is not designed correctly for the resonator and target IC. Spurious oscillation is basically any oscillation not occurring at the resonator's specified oscillation frequency (for example: a 4MHz resonator is used, but the circuit oscillates at 12MHz). Table 2 lists the possible causes for spurious oscillation for various frequency ranges of resonators.
General Resonator
Series
CSB
CSA-MK
CSA-MG CST-MG CSA-MG CSTLS-G CSA-MG CSTS-MG CSA-MTZ CST-MTW CSA-MXZ CST-MX
CSALS-MX CSTLS-X
Frequency Range
375k - 580kHz 581k - 910kHz 911k - 1250kHz
1.26M 1.79MHz 1.80M 1.99MHz
2.00M - 3.39
3.40M 10.00MHz 10.01M 13.00MHz
13.01M 15.99MHz
16.00 70.00MHz
Vibration Mode
Possible Cause of Irregular Oscillation
Type 1 (Spurious Response)
Type 2 (Other)
Area Area Area
3rd Overtone, Thickness vibration (at 4.3MHZ) 3rd Overtone, Thickness vibration (at 5.7MHZ) 3rd Overtone, Thickness vibration (at 6.5MHZ)
Shear
3rd Overtone (not common)
Thickness Shear
3rd Overtone (not common)
Thickness Shear
3rd Overtone (not common)
Thickness Shear
3rd Overtone (not common)
Thickness Longitudinal
3rd Overtone (not common)
Thickness Longitudinal Third Overtone
Fundamental and 5th Overtone
Thickness Longitudinal Third Overtone
Fundamental and 5th Overtone
Table 2. Possible Causes of Irregular Oscillation
CR Oscillation LC Oscillation Ring Oscillation
Irregular oscillations can be classified into two basic type by their causes: Type 1: Oscillation occurring at the spurious response of the resonator. Type 2: RC, LC, or Ring oscillation.
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PZT Application Manual
Type 1 Irregular (Spurious) Oscillation
For ceramic resonators utilizing natural 3rd overtone operation, a greater chance is present for fundamental and 5th overtone spurious oscillations. If a LC tank circuit is used (like with quartz resonators) the chance for spurious oscillations is almost zero. However, Murata 3rd overtone resonators are designed to not need an external tank circuit. For kHz resonators that have problems with third overtone or thickness vibration mode spurious oscillations, the solutions for 5th overtone oscillations mentioned below can correct these spurious oscillations as well.
Fundamental Oscillation
Increasing the loop gain at the 3rd (main) response, decreasing loop gain at the fundamental, and decreasing the phase shift at the fundamental are possible solutions to fundamental spurious oscillations
· Decrease the load capacitor capacitance. This will increase the gain seen at the main response (3rd). Decreasing load capacitance too much can result in 5th overtone oscillation.
· Decrease Rf to a few k (10k - 30k). This will dump the resonator's response, especially at the fundamental.
5th Overtone Oscillation
To remove 5th overtone oscillation (or 3rd overtone oscillation for fundamental resonator), it is necessary to decrease the loop gain at this overtone.
· Increase the value of the load capacitors. This will reduce gain at the 5th overtone (or 3rd overtone for fundamental resonators). This does have the small effect of decreasing gain at the main response, so increasing load capacitance too much can send the 3rd overtone resonator in to fundamental oscillation (or the fundamental into an unexpected LC or RC oscillation).
· Add or increase the value of the existing Rd resistor. Increasing or adding Rd will decrease gain across all frequencies. If an oscillation circuit has abundant gain at the main (or fundamental) response, then the circuit could withstand increase to Rd in order to dampen the overtone oscillation. Also, Rd and CL2 act like a low pass filter, dampening gain at higher frequencies.
· Connect bypass capacitors to the voltage supply pin of the IC to remove high frequency noise during power up of the oscillation circuit.
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Type 2 Irregular (Spurious) Oscillation:
In the case of type 2 spurious oscillation, the resonator is acting like a capacitor at a capacitance value close to the resonator's shunt capacitance, Co. For RC spurious oscillation, the resonator's shunt capacitance and the amplifier's (or inverter's) input impedance act like a RC circuit causing unwanted oscillation. For LC spurious oscillation, the resonator's shunt capacitance and stray inductance in the circuit act like a LC circuit causing unwanted oscillation. These types of spurious oscillations are hard to identify, since this spurious oscillation usually occurs at very high or very low frequencies (not near the intended oscillation frequency). Many resonator circuits that appear not to oscillate at resonator's specified oscillation frequency (circuit appears to be dead, no oscillation) are actually oscillating at a very high frequency in a spurious oscillation mode. One way to confirm that this type of spurious oscillation is occurring is to replace the resonator with a capacitor of the same value as the resonator's shunt capacitance. If the circuit continues to have the same frequency oscillation after the resonator / capacitor swap, then the oscillation can be attributed to LC or RC oscillation. A common cause of RC, LC, or ring oscillation is too much amplifier gain, most notably from using buffered inverters. A buffered inverter is typically three non-buffered inverters in series. Because of this, buffered inverters have a considerable amount of gain, resulting in these types of spurious oscillations. Murata recommends only using unbuffered inverters for oscillation circuits using ceramic resonators. Most clock circuits in current ICs use unbuffered type inverters. You can still feed the output of the unbuffered oscillation circuit into another unbuffered inverter to square up the output waveform from the oscillation circuit. Ring oscillation typically occurs when there is too much phase shift through the amplifier (or inverter). Ring type oscillation really only occurs when using the unrecommended buffered inverter as the amplifier. Due to the three inverter stages in a buffered inverter, a substantial amount of phase delay is introduced to the circuit, causing the ringing. To stop ring oscillation, switch to an unbuffered inverter. If changing to a unbuffered inverter does not stop the type 2 oscillation (or you are already using an unbuffered inverter), we must try alternate techniques to make these spurious oscillation no longer meet Barkhausen Criterion for oscillation. The following may be used to do this:
· Try changing the load capacitor values. By increasing the load capacitor values, the high frequency circuit gain is reduced without major impact to the gain at fundamental. Increasing load caps too much can result in the circuit not being able to oscillate even at the fundamental response.
· Try unbalancing the load cap values. For most applications, the two load capacitors are basically the same value. Having load capacitors at two different values can sometimes correct type 2 spurious oscillations.
· Try adding a Rd or increasing Rd (if already present in the oscillation circuit). Rd has the effect of decreasing circuit gain across all frequencies (unlike changing load capacitor values). This is a more drastic method, since the gain at the fundamental response is decreased as well as gain at the spurious oscillations.
· Try adding a bypass capacitor to the power line to the IC to remove any external noise coming into the oscillation circuit.
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PZT Application Manual
IC Characterization Service
The ceramic resonators produced by Murata (or any ceramic resonator maker) may or may not work with all ICs using standard external circuit values. This is mainly due to typical variations in ICs and resonators, part to part. In order to assist our customers with their designs, Murata offers a resonator / IC characterization service free of charge. The customer's IC is tested with the Murata resonator. Measurements are made to determine frequency correlation between the standard sorting ICs Murata uses in production and the customer's IC. Based on test results and Murata's long experiance with ceramic resonators / oscillation circuits, Murata provides the recommended Murata part number that should be used with their target IC and the recommended external hook up circuit for this target IC. This recommendation insures that the IC / resonator combination will have stable oscillation and good start up characteristics (taking into account any resonator that could be shipped to the resonator specification) This enables the designers to adjust their designs so that the resonator will work every time. These adjustments can be as simple as adjusting component values or as complicated as redesigning the entire circuit. If the recommendations made by Murata are followed then the resonator is guaranteed to work every time. Besides looking at oscillation stability, Murata can also test for freqeuncy correlation between customer target IC and Murata's production sorting circuit. Murata Electronic Sales representatives are able to arrange IC characterizations. Please try to start the IC characterization process with Murata as soon as possible, since it does take time to do an IC characterization and there can be several customers at any one time waiting for this service. Please see Appendix 3 for more information on this service and needed forms.
Characteristics of Oscillators Using A Ceramic Resonator
The next sections explain some of the characteristics of oscillation circuits using ceramic resonators.
Oscillation Rise Time
The rise time is the time it takes for oscillation to develop from a transient area to a steady state area at the time the power is applied to the circuit. It is typically defined as the time to reach 90% of the oscillation level under steady conditions. Figure 20 illustrates the rise time.
ON
VDD
0V
0.9VPP
VPP
T=0 Rise Time Time
Figure 20: Diagram of Oscillation Rise Time
This area is important because without a fully developed signal, mistakes could be introduced into the digital computations in the IC. An ideal circuit would have no rise time, meaning that it would instantaneously power up and reach steady oscillation. An advantage of ceramic resonators is that the rise time is one or two decades faster than quartz
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crystal (Figure 21).
Crystal Resonator
Ceramic Resonator
Figure 21: Comparison of Oscillation Rise Time Between Ceramic Resonator and Quartz Crystal Resonator
Starting Voltage The starting voltage is the minimum supply voltage at which an oscillating circuit will begin to oscillate. The starting voltage is affected by all circuit elements but is determined mostly by the characteristics of the IC.
Speciality Resonator Applications Telephone (D.T.M.F)
It is becoming more and more common to use the telephone keypad for data transmission. It is used to make selections on automated answering systems, for example. It is also becoming more important to ensure that the button pressed will be registered as the corresponding number by the receiving end. When a telephone key is pressed, a certain audible frequency is generated representing that key. It is critical that the frequency generated is accurate, so the receiving end understands what key was pressed. For this reason, a global regulation calls for a mandatory frequency tolerance. The total allowable frequency tolerance for the oscillation of a tone dialer for a telephone is ±1.5%. This tolerance is for the IC as well as the resonator, not just the resonator alone. Table 3 shows how the tolerance is divided up between the IC and the resonator.
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PZT Application Manual
IC
Dividing Error [+0.7% ~ +0.8%
Resonator
Temp. Stability [+0.2%]
Aging [+0.1%]
Variance against Loading Cap. Tol. [+0.1%]
Margin
[+0.1% ~ +0.2%]
Initial Tolerance [+0.1% ~ +0.3%]
Fixed Value
Circuit Margin (Rank)
This initial tolerance is calculated with total allowable frequency tolerance, above fixed values, and safety margin.
Table 3. DTMF Tolerance Chart
The typical resonator frequency used is 3.58MHz. This frequency is divided by the IC to generate the lower frequency audible tones associated with each key press. The dividing error is related to the IC that is used in the circuit and so is a fixed value. This value will usually be specified on the data sheets for the IC. Aging of the resonator is also a fixed value. The other values can be changed by changing the design of the resonator. Murata has developed a way to account for the different tolerance specifications on our parts. We add a postscript to
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the part numbers based on the chart in Figure 22.
CSA3.58MG300( ) CST3.58MGW300( )
3.5795MHz
-0.6 -0.5 -0.4 -0.3 -0.2 -0.1
+0.1 +0.2 +0.3 +0.4 +0.5 +0.6 (Unit:%)
-0.55
F
-0.30
MARKING PURPLE
CSA3.58MG300F CST3.58MGW300F
-0.25
A
+0.00
MARKING BLACK CSA3.58MG300A CST3.58MGW300A
+0.05
C
+0.30
MARKING RED
CSA3.58MG300C CST3.58MGW300C
+0.35
E
+0.60
MARKING WHITE
CSA3.58MG300E CST3.58MGW300E
-0.40
G
-0.15
MARKING GREEN
CSA3.58MG300G CST3.58MGW300G
-0.10
B
+0.15
MARKING BLUE
CSA3.58MG300B CST3.58MGW300B
+0.20
D
+0.45
MARKING ORANGE
CSA3.58MG300D CST3.58MGW300D
CSTS0358MG3**** CSTCC3.58MG3****
3.5795MHz
(Unit:%)
-0.9 -0.8 -0.7 -0.6 -0.5 -0.4 -0.3 -0.2 -0.1
+0.1 +0.2 +0.3 +0.4 +0.5 +0.6
-0.725
-0.475
RANK : 2
-0.425
-0.175
RANK : 4
-0.125
+0.125
RANK : 6
+0.175
+0.425
RANK : 8
-0.875
-0.625
RANK : 1
-0.575
-0.325
RANK : 3
-0.275
-0.025
RANK : 5
+0.025
+0.275
RANK : 7
+0.325
+0.575
RANK : 9
Figure 22: DTMF 3.58MHz Resonator Tolerance Chart
For example, a part with a tolerance of ±0.1% would have ABC at the end of its part number. Murata is able to produce resonators with asymmetrical tolerances (i.e. +0.1%, -0.2%) and this convention provides an easy way to label the parts. Resonators for various commerically available DTMF ICs have already been characterized by Murata and resonator part number recommendation are available. If a particular DTMF IC has not been characterized yet by Murata, this can be handled in the same way as the common IC characterization service Murata provides.
Voltage Controlled Oscillator (VCO) Circuits
VCO circuits are used in TV and audio equipment to process signals in synchronization with reference signals transmitted from broadcasting stations. They use a DC input voltage to change the frequency of oscillation. For example, if a VCO operates at 4 MHz with a 0V DC input, then it might operate at 4.01MHz with a 1V DC input. VCOs work by varying either the resonant or anti-resonant frequencies of the resonator. To change the resonant frequency, a varactor diode is placed in series with the resonator. Changing the capacitance of the diode changes the resonant frequency of the resonator. Adding positive or negative reactance in parallel with the resonator will change the anti-resonant frequency. Since ceramic resonators have a wide F compared to quartz crystal, they are more easily used in VCO designs. The wider F allows for a greater range of frequencies the resonator can be changed to. Two examples of VCO applications are TV horizontal oscillator circuits and stereo multiplexer circuits. Like the DTMF ICs, Murata has many of the ICs requiring VCO resonators already characterized. If an IC has not been characterized with a Murata resonator, then an IC characterization will need to be performed.
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PZT Application Manual
Part Numbering
This section will go over Murata part number construction and how to make a ceramic resonator part number. Due to the myriad of resonator part numbers possible, this section will not cover every possible part, but should cover at least 85% to 90% of them. Figures 23 and 24 show examples of the structure for the Murata part numbering systems for the kHz and MHz resonators.
CSB 1000 J ---
Series
See list of available kHz series
Frequency (kHz)
Frequency ranges from 190 to 1250kHz
Construction D or J = Washable E or P = Non Washable
Frequency Tolerance Blank or 0 = + 0.5%
100 = + 0.3% 800 = + 1.0%
Figure 23: kHz Part Numbering System
CSA 3.58 MG 1 00 -Txxx
Series Frequency Type
Tolerance
Denotes sorting IC circuit
(MHz)
Blank or 0 = + 0.5% and built-in load cap value
See list of
1 = + 0.3%
(CST series only for built-in
available
8 = + 1.0%
load caps)
MHz series
Blank or 00 = CMOS
40 = HCMOS sorting circuit
Tape Options
-TF01 or -TR01 for leaded parts -TC for SMD parts
Figure 24: MHz Part Numbering System
How To Make a Resonator Part Number.
This next section will step you through making a Murata ceramic resonator part number.
· Determine Resonator Series Table 4 lists the different resonator series offered by Murata. In the table for each listed series, we advise applicable frequency range, built-in load cap status, if the part is SMD or leaded, and if the part is washable. Please note that the second part of Table 4 list those resonators available in the automotive temperature range (adds an "A" to the suffix).
· Make the Base Part Number From Table 4, you have picked your series. The Resonator Series column in Table 4 indicates the part prefix and suffix. Between the prefix and suffix, you need to add the frequency (where you see the "..."). You will note that SMD parts already have the taping suffix attached since SMD parts are only supplied on tape and reel (bulk SMD parts is not an option).
· Add the Frequency Based on the series selected, the Frequency Range column will advise available frequency range Frequency Rules:
1) kHz filters can have either 3 or 4 digits total, with no decimal places. (Example: 455 or 1000, but not 355.6 or 10.00) 2) MHz MG resonators can have three digits total, with two decimal places. (Example: 3.58 or 6.00, but not 3.586) 3) MHz MT resonators can only have three digits total, with one or two decimal places. (Example: 8.35 or 10.5, but not 8.356 or 10.55)
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4) MHz MX resonators can only have 4 digits total, with two decimal places. (Example: 15.00, 55.25, but not 20.386 or 50.4567)
· Taping For SMD parts, the series already includes the taping. Leaded kHz resonators do not have a taping option. We can supply some leaded kHz filters in tubes, but you will need to confirm availability with Murata. For leaded MHz resonators, the parts can be supplied on tape and ammo box (-TF01, our standard and most available taping option for leaded resonators) or tape and reel (-TR01).
· Conclusion For 80% of the part numbers, you are done making your part number by this step. The only additional options you may need to pick is initial frequency tolerance (MHz and kHz resonator, see Figures 23 and 24), IC sorting circuit (see Figures 23 and 24), and any additional suffixes (including resonators for VCO and DTMF applications).
· General Part Numbering Rules Here is a list of general part number rules, that really do not fit into the above instructions:
1) A resonator will never have a suffix with "000" in it. This suffix calls out (first digit) initial frequency tolerance and (last two digits) IC sorting circuit / built-in load cap values. If this final suffix turns out to be "000" (with or without taping suffix), the "000' is dropped completely (Example: CSA4.00MG and CSA4.00MG-TF01 correct, CSA4.00MG000 and CSA4.00MG000-TF01 incorrect).
Resonator Series
Frequency Range (Hz)
Load Caps Included
SMD
Washable
CSB...P
375k - 429k & 510k 699k
N
N
N
CSB...E
430k - 509k
N
N
N
CSB...J
375k - 429k &
430k - 519k &
520k - 589k &
N
N
Y
656k - 699k &
700k - 1250k
CSB...JR
590k - 655k
N
N
Y
CSA...MK
1.26M - 1.799M
N
N
Y
CSA...MG
1.80M - 6.30M
N
N
Y
CSA...MTZ
6.31M - 13.0M
N
N
Y
CSA...MXZ
13.01M - 15.99M
N
N
Y
CSALS-X
16.00M - 70.00M
N
N
Y
CST...MG
1.80M - 1.99M
Y
N
Y
CSTLS-G
2.00M - 3.39M
Y
N
Y
CSTS...MG
3.40M - 10.00M
Y
N
Y
CST...MTW
10.01M - 13.0M
Y
N
Y
CST...MXW040
13.01M - 15.99M
Y
N
Y
CSTLS-X
16.00M - 70.00M
Y
N
Y
CSBF
430k - 1250k
N
Y
Y
CSAC...MGC-TC
1.80M - 6.00M
N
Y
Y
CSAC...MGCM-TC
1.80M - 6.00M
N
Y
Y
CSACV...MTJ-TC20
6.01M - 13.0M
N
Y
Y
CSACV...MXJ040-TC20
14.00M - 20.00M
N
Y
Y
CSACW...MX01-TC
20.01M - 70.00M
N
Y
Y
CSTCC...MG-TC
2.00M - 3.99M
Y
Y
Y
CSTCR-G-R0
4.00M - 7.99M
Y
Y
Y
Table 4. Available Resonator Frequencies by Series (Package)
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PZT Application Manual
CSTCC...MG-TC
8.00M - 10.00M
Y
Y
Y
CSTCV...MTJ-TC20
10.01M - 13.0M
Y
Y
Y
CSTCV...MXJ0C4-TC20
14.00M - 15.99M
Y
Y
Y
CSTCW...MX03-T
16.00M - 60.00M
Y
Y
Y
Automotive ("A" suffix.)
CSB...JA
375k - 1250k
N
N
Y
CSBF...JA
430k - 1250k
Y
N
Y
CSA...MGA
1.80M - 6.30M
N
N
Y
CSA...MTZA
6.31M - 13.0M
N
N
Y
CSA...MXZA040
13.01M - 15.99M
N
N
Y
CSALS-X-A
16.00M - 70.00
N
N
Y
CST...MGA
1.80M - 1.99M
Y
N
Y
CSTLS-G-A
2.00M - 3.39M
Y
N
Y
CSTS...MGA
3.40M - 10.00M
Y
N
Y
CST...MTWA
10.01M - 13.0M
Y
N
Y
CST...MXWA040
13.01M - 15.99M
Y
N
Y
CSTLS-X-A
16.00M - 70.00M
Y
N
Y
CSAC...MGCA-TC
1.80M - 6.0M
N
Y
Y
CSAC...MGCMA-TC
1.80M - 6.0M
N
Y
Y
CSACV...MTJAQ-TC
6.01M - 13.0M
N
Y
Y
CSACV...MXAQ-TC
13.01M - 70.00M
N
Y
Y
CSTCC...MGA-TC
2.0M - 3.99M
Y
Y
Y
CSTCR-G-A-R0
4.00M - 7.99M
Y
Y
Y
CSTCC...MGA-TC
8.00M - 10.00M
Y
Y
Y
CSTCV...MTJAQ-TC
10.01M - 13.0M
Y
Y
Y
CSTCV...MXAQ-TC
13.01M - 70.00M
Y
Y
Y
Table 4. Available Resonator Frequencies by Series (Package)
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The parts may have an additional suffix that refers to a special aspect of the part. Table 5 gives a list of these suffixes.
Suffix
Meaning
A
For Automotive
B
Bent Lead Type
F
For V.C.O Applications
3xx
DTMF part, usually at frequency of 3.58MHz, leaded or SMD.
P
Custom marking on part
Short Lead Type (std. = 5.0 + 0.5mm)
S = 3.8 + 0.5mm
Sx
S1 = 3.5 + 0.5mm
S2 = 3.4 + 0.5mm
T
Lead Forming Type (Gull Wing Style)
U
Low Supply Voltage
Additional Color Dot (Top Left) Must check with Murata for availability.
Y0 = Black
Y5 = Green
Yx
Y1 = Brown
Y6 = Blue
Y2 = Red
Y7 = Purple
Y3 = Orange
Y8 = Gray
Y4 = Yellow
Y9 = White
Table 5. Resonator Part Number Suffix
The CSTS series and the CSACW/CSTCW series follow the part numbering system in Figure 25. Although the system includes numbers for several values of load capacitors, currently only 15pF and 47pF values are available for the CSTS series, and 5pF and 15pF values are available for the CSTCW series.
CSTS 0400 MG 0 3 001
Series
See list of available
series
Frequency (MHz)
Type
Tolerance 0 = + 0.5% 1 = + 0.3% 2 = + 0.2% 8 = + 1.0%
Load Cap Value CustomMark 1 = 5pF 2 = 10pF 3 = 15pF 4 = 22pF 5 = 30pF 6 = 47pF
Figure 25: Resonator Part Numbering System
Beginning in the summer of 2000, a new gloabal part numbering system will be implemented by Murata. All resonators introduced in 2000 and later will follow this part numbering system, and some current resonators will be switched to this
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PZT Application Manual
system.
Type of part
CS --> Ceramic Resonator
Terminal Form
L or R Leaded
C Chip
F
Quasi SMD
B Bare Chip
Frequency
Vibration Mode
Custom Specification
4 digits
E
Square
2 digits, Blank, 01 to 99,
2.00MHz -> 2M00 G
Share
A1 to A9, ..., Z1 to Z9
T
Thickness (1st)
X
Thickness (3rd)
V
2nd Harmonics
CS T L S 2M00 G 5 6 A 01 -B0
Packaging -B0 Bulk -A0 Ammo Box, Ho=18mm -A1 Ammo Box, Ho=16mm
-R0 Reel, =180mm -R1 Reel, =330mm
With Or Without Size
Load Caps
Leaded type S
B kHz 2 terminals Gullwing type B
A MHz 2 terminals Chip type
T MHz 3 terminals 7.2 x 3.0
C
4.5 x 2.0
R
3.7 x 3.1
V
2.5 x 2.0
W
3.2 x 1.25 E
6.0 x 2.5
D
2.0 x 1.25 S
Initial Tolerance
1
±0.1%
2
±0.2%
3
±0.3%
4
±0.4%
5
±0.5%
6
±0.6%
7
±0.7%
8
±0.8%
9
±0.9%
B
±1kHz
C
±2kHz
D
DTMF
Load Cap Value*
1
5pF
2
10pF
3
15pF
4
22pF
5
33pF
6
47pF
7
68pF
8
100pF
9
150pF
B
220pF
C
330pF
D
470pF
E
120 + 470pF
F
220 + 470pF
G
330 + 470pF
Z
Others
Custom Form Specification**
Blank Consumer Grade
A
Automotive Grade
B
Bent Lead
E
0.5mm Height
F
VCO
L
Long Lead
P
Custom Marking
Q
High Reliability
R
Custom Dip Dimension
S
Short Lead
W
Washable
C
A + S
D
A + P
* Note: Not all load cap values available with a specific part. In the case of 2 terminal resonators, cap value is for Murata standard circuit. In the case of 3 terminal resonators, cap value is for built-in capacitors.
** Note: Not all custom forms are available with a specific part.
Figure 26: New Resonator Part Numbering System
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Page 28
Figure 27: kHz Resonator Selection Guide PZT Application Manual
VCO Applications
Leaded
START kHz Resonator
Non-VCO Applications
VCO Applications
Surface Mount
Washable
Non-washable
CSBF...JFx-TC01
Non-VCO Applications
CSBF...J-TC01
Washable
Non-washable
CSB...J CSB...JR
CSB...JFx
CSB...Fx
CSB...E CSB...P
x represents a number that calls out the IC that this part works with. VCO resonators are IC specific so only work with certain IC
chips.
PZT Application Manual
Figure 28: MHz Resonator Selection Guide
Leaded
START MHz Resonator Parts In Parentheses () Are Automotive Grade
Surface Mount
Without Built In Load Capacitors
Built In Load Capacitors
Without Built In Load Capacitors
Built In Load Capacitors
.26MHz to
.79MHz
.80MHz to
.44MHz
2.45MHz to
6.30MHz
6.31MHz to
3.00MHz
3.01MHz to
5.99MHz
6.00MHz to
0.00MHz
CSA...MK
CSA...MG (CSA...MGA)
10 x 10 x 5 10 x 12 x 5
CSA...MG (CSA...MGA)
7.5 x 10 x 5
CSA...MTZ (CSA...MTZA)
10 x 10 x 5
CSA...MXZ040 (CSA...MXZA040)
10 x 10 x 5
CSALS..M...X (CSALS..M...X...A)
5.5 x 6.5 x 3.5
1.80MHz to
1.99MHz
2.00MHz to
3.39MHz
3.40MHz to
10.00MHz
10.01MHz to
13.00MHz
13.01MHz to
15.99MHz
16.00MHz to
70.00MHz
CST...MG (CST...MGA)
10 x 12 x 5
CSTLS...MG (CSTLS...MGA)
5.5 x 8 x 3
CSTS...MG (CSTS...MGA)
5.5 x 8 x 3
CST...MTW (CST...MTWA)
9 x 10 x 5
CST...MXW040 (CST...MXWA040)
9 x 10 x 5
CSTLS..M...X (CSTLS..M...X...A)
5.5 x 6.5 x 3.5
1.8MHz to
6.00MHz
CSAC...MGC/MGCM-TC (CSAC...MGCA/MGCMA-TC)
CSAC-MGC 2.8 x 7.0 x 2.8
2.00MHz to
3.99MHz
CSTCC...MG-TC (CSTCC...MGA-TC)
3.0 x
6.01MHz to
13.00MHz
14.00MHz to
20.00MHz
20.01MHz to
70.00MHz
CSAC-MGCM 2.85 x 7.0 x 2.85
4.00MHz to
7.99MHz
CSTCR..M...G-R0 (CSTCR..M...G...A-R0)
CS 2.0 x
CSACV...MTJ-TC20 (CSACS...MTA-TC)
CSACV 3.1 x 3.7 x 1.7 (*1)
8.00MHz to
10.00MHz
CSACV...MXJ040-TC20 (CSACS...MXA040Q-TC)
CSACS 4.1 x 4.7 x 2
10.01MHz to
13.00MHz
CSTCC...MG-TC (CSTCC...MGA-TC)
C 3.0 x
CSTCV...MTJ-TC20 (CSTCS...MTA-TC)
C 3.1 x 3
CSACW...MX-T (CSACS...MXA040Q-TC)
CSACW 2.0 x 2.5 x 1. 2
14.00MHz to
20.00MHz
CSTCV...MXJ-TC20 (CSTCS...MXA040Q-TC)
CST
4.1 x
20.01MHz to
70.00MHz
CSTCW...MX-T (CSTCS...MXA040Q-TC)
2.0
OTE: art dimensions are H x W x T in mm
1) Thickness varies with frequency and load capacitance
Page 29
Piezoelectric Filters
Introduction
As you may know, we are constantly surrounded by all sorts of radio frequencies. From audio range frequencies that we can hear to very high frequencies that are visible as light, our electronics and we are constantly being immersed in these frequencies. It is the job of a band pass filter to pick out only the range of frequencies desired for the intended application. Ideally, when an inputted signal (say from an antenna) goes through a band pass filter, all frequencies that are within the bandwidth ("pass-band") of the filter will be allowed to pass through the filter. Those frequencies above or below the pass-band region (in the "stop-band") will be attenuated (or rejected) at some fixed value (determined by the filter) and thus will not be seen at the output of the filter. Figure 29 visualizes the effect of an ideal band-pass filter.
Amplitude Amplitude
Input to the filter
Output of the filter
Original Level Ideal Band Pass Filter
IDEAL
Frequency
Frequency
Figure 29: Ideal Band Pass Filter
As you can see in Figure 29, all frequencies are allowed to enter the filter but only those frequencies within the passband are allowed to exit the filter unattenuated (or unaffected). One would expect that the band of frequencies passed by the filter would leave the filter unaffected, but this is not the case for a practical band-pass filter. There are many parasitic losses associated with a practical band-pass filter, such as insertion loss, ripple, and non-ideal roll off. Figure 30 visualizes the effect of a practical band-pass filter on a signal.
Amplitude Amplitude
Input to the filter
Output of the filter
Practical Band Pass Filter
Original Level
Frequency
Practical
Frequency
Figure 30: Practical Band Pass Filter
As you can see from comparing Figure 29 to Figure 30, the output of the filter is quite different. First you will notice that the signal level of the output signal in Figure 30 is less than the original signal level. This is due to the inherent loss (or insertion loss) of the filter. You will also notice that the sides of the pass-band in Figure 30 are not vertically straight, as in Figure 29. Practical filters, as in Figure 30, can not achieve such performance. The response will always look rounded. Very selective filters will have roll off approaching that of an ideal filter, but will trade off performance in other key filter performance parameters. One very important parasitic effect not shown in Figure 30 is Group Delay Time (GDT). The next section will cover this important effect.
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PZT Application Manual
Group Delay Time (GDT)
For this discussion we are only concerned with the effect of GDT on the frequencies being allowed to pass through the band pass filter. We are looking at this characteristic specifically since it is the hardest to understand. In a practical band-pass filter, the filter actually causes the passed frequencies to be delayed slightly in time as they pass through. The delay time is not constant across the pass-band and the frequencies end up being delayed by differing amounts of time. Frequencies occurring close to the center frequency of the filter are delayed the least while frequencies closer to the edges of the pass-band are delayed more. This delay effect is referred to as Group Delay Time (GDT). Since the frequencies are effected in time, the phase of the frequencies in relation to each other is changed. Hence, the term phase delay is sometimes used as a synonym to GDT. Figure 31 visualizes this delay effect.
High Frequency Low High Frequency Low
Input to the filter
Lower Edge of Pass Band
Output of the filter
Center of Pass Band
Band Pass Filter
Upper Edge of Pass Band
Time = t
Time = t + 1
Figure 31: Group Time Delay
In Figure 31, we see a series of frequencies (we will only look at frequencies occurring within the pass-band of the filter, even though other frequencies are entering the filter as well) just prior to entering the filter. The frequencies are all aligned at the same point in time. Think of this like a horse race and each arrow (representing a frequency) is a horse. At time "t", all of the horses are at the starting gate. The race starts and the horses / frequencies enter the filter. At the end of the race (time now equals "t+1", or some time in the future), as shown at the "output of the filter" in Figure 31 above, the horses / frequencies that traveled near the center of the filter's pass band leave the filter first. Those horses / frequencies near the upper and lower edges of the filter's pass-band are delayed compared to the horses / frequencies at the center. The horses / frequencies at the pass-band edges have been delayed in time. This means that the filter imparts some time delay to frequencies in the pass-band. This effect can be considered a form of distortion since the filter is modifying the frequencies it should pass. Ideally, the filter should not effect the signal in the pass band at all. In purely analog systems, this GDT is not too devastating. GDT generally causes distortion of the signal but usually not to the point of adversely effecting the analog system. In a digital system, however, GDT can be devastating if the delay is too great. The heart of a digital system is the square wave (pulse). The square wave is composed of many sine waves of various frequencies (harmonics). The higher and lower sine wave frequencies form the squared off shoulders and the steep transition point. The frequencies most important to a square wave's shape are the frequencies usually effected the most by the GDT effect. This effect can degrade the square wave to a point where it loses all meaning to a digital system. For a digital system engineer, this means that his Bit Error Rate (BER) will suffer. A band pass filter's characteristics have a significant effect on the magnitude of GDT deviation that occurs between the delay times of each frequency in the pass-band. A band-pass filter with a Butterworth type response has poor GDT performance but has good selectivity and a flat pass-band. The Butterworth response is characterized by a flat pass-band
PZT Application Manual
Page 31
with relatively sharp roll-off (Figure 32a).
Amplitude Time
Amplitude Time
Large GDT Deviation
Frequency (a) Butterworth Filter
Small GDT Deviation
Frequency (b) Gaussian Filter
Figure 32: Types of Band Pass Filter
The GDT of this type of filter is characterized by a large deviation time between the frequencies around the center frequency and the frequencies at the pass-band edges. A band-pass filter with a Gaussian type response has good GDT performance, but only moderate selectivity (Figure 32b). The Gaussian response is characterized by a rounded pass-band with moderate roll-off. The GDT of this type of filter is characterized by a small deviation time between the frequencies around the center frequency and the frequencies at the pass-band edges. One important point to make is this: if all frequencies in the pass-band were delayed by the same amount of time, the overall negative effect to the system (analog or digital) is diminished.
GDT Specification
In the specification for a filter that has controlled GDT characteristics, Murata specifies GDT deviation as opposed to absolute GDT. Absolute GDT references all measurements from the time a signal is inserted into the filter. GDT deviation refers to the time difference from the first frequency out of the filter to the last frequency out of the filter, for a given signal. GDT deviation is a better measurement since the most important information is how the frequencies deviate from each other in time. In all GDT measurements, the unit of measure is time (usually in nanoseconds or microseconds) over a given bandwidth. Here is an example of a GDT spec: 25µS max over ±30kHz (referenced to fo).
Other Band Pass Filter Characteristics
Figure 33 shows the response plot of the output from a band pass filter. The various band pass characteristics of inter-
Page 32
PZT Application Manual
est are labeled and numbered. The explanation for each of these characteristics is shown in the table.
Attenuation (dB)
Input Level
0
3 4
(1) Center Frequency (fo) (2) Pass Bandwidth
6
(3dB BW)
3
F3L 2 F3H
7 (3) Insertion Loss (4) Ripple
8
(5) Attenuation Band
Width
X
5
FXL
FXH
1 Fo
(6) Selectivity (7) Spurious Response
(8) Stop Band Attenuation
Frequency
Figure 33: Band Pass Filter Characteristics
· Center Frequency The frequency in the center of the pass band. To calculate the center frequency, use the following equation (some symbol notation is from Figure 33):
Fo = F 3L - F 3H 2
Example: Fo = 455kHz
· Pass-Bandwidth This is the difference between the two frequencies (F3L and F3H) that intersect a horizontal line 3dB down from the point of minimum loss. Depending on the filter type, some filters specify the 6dB bandwidth instead of the 3dB bandwidth. In this case, the horizontal line used to intersect the frequency plot is 6dB down from the point of minimum loss. Example: 3dB B.W. = 60kHz total or ±30kHz (referenced to fo).
6dB B.W. = 64kHz total or ±32kHz (referenced to fo).
· Insertion Loss The minimum loss for a given input signal associated with the given filter. It is expressed as the input/output ratio at the point of minimum loss. The insertion loss for some filter products is expressed as the input/output ratio at the center frequency. Example: I.L. = 5dB max.
· Ripple If there are peaks and valleys in the pass band, the ripple is expressed as the difference between the maximum peak and the minimum valley. Example: Ripple = 1dB max.
· Attenuation Bandwidth Attenuation bandwidth is the bandwidth of the pass-band at a specified level of attenuation. This is similar to the 3dB or 6dB bandwidth except that the attenuation level used is significantly higher, usually 20dB or larger. In Figure 33, it is the difference between FXL and FXH where "X" is the attenuation level.
PZT Application Manual
Page 33
Example: 40dB B.W. = 100kHz total or ±50kHz (referenced to fo).
· Stop Band Attenuation Stop band attenuation is the maximum level of strength allowed for frequencies outside of the pass-band. Example: Attenuation 455 ±100kHz = 35dB min.
· Spurious Response The spurious response is the difference in decibels (dB) between the insertion loss and the spurious response in the stop band (area not in the specified pass-band). Example: Spurious Response = 25dB min.
· Input / Output Impedance The input and output impedances are the impedance values that the filter should be electrically matched to at the filter's input and output, respectively. Example: I/O impedance = 1K
· Selectivity The selectivity is the ability of a band pass filter to pass signals in a given frequency bandwidth and reject (or attenuate) all frequencies outside of the given bandwidth. A highly selective filter has an abrupt transition between the pass-band region and the stop band region. This is expressed as the shape factor, which is the attenuation bandwidth, divided by the pass bandwidth. The filter becomes more selective as the resulting value approaches one.
Connecting Filters In Series
It is sometimes helpful to increase outband attenuation by connecting filters in series. If the input and output impedances of the filters are equal, then the filters may be connected directly to each other. If they have different impedances, a matching circuit may be necessary. The main advantage to connecting filters in series is that there is a much better spurious response attenuation and outband attenuation. Some disadvantages are that insertion loss, GDT, and ripple are all additive. The differences between worst case and best case for each specification can cause a wide variation in these specifications when they are added. For example, if the insertion loss of a filter is specified to be between 3 and 6dB, then when they are added the insertion loss will be between 6 and 12dB. The main disadvantage is that the center frequency variations part to part can decrease the absolute bandwidth of the combination of filters. As can be seen in Figure 34, if the center frequencies are slightly off, then the absolute bandwidth will be between the lower end of the filter that is centered higher and the upper end of the filter that is centered lower.
Filter 1 Passband
Resulting Bandwidth
Filter 2 Passband
Figure 34: Resulting Bandwidth When Cascading Filters
The resulting center frequency will be somewhere between the two filters. For some applications this is not a large problem and is cheaper than buying filters with more elements.
Page 34
PZT Application Manual
PZT Band Pass Filters
Filter types available
The PZT group of Murata only offers band pass filters. We offer band pass filters with the following center frequencies: · 450kHz or 455kHz · 10.7MHz and 4.5 to 6.5MHz (Sound IF applications for video)
Note: Murata's PZT group also makes band pass filters from 3.58MHz to 6.5MHz, but these filters are typically for video / TV applications only. We can also offer VIFSAW filters, which are band pass filters too, but are also for video / TV applications specifically. There is a specific application manual for these video products, but the concepts for band pass filters apply to these products as well.
Most filters are available in both leaded and surface mount (SMD) packages. Certain specialty filters are only available in leaded packages. The next section will display the variety of Murata filters available at 450/455kHz and 10.7MHz, and each filter's basic electrical specifications
PZT Application Manual
Page 35
kHz Filters
Introduction
The kHz ceramic filters were originally designed for AM radio applications that used 450kHz or 455kHz as a radio IF frequency. In the past, engineers would use tunable coils to achieve the required IF filtering for AM radios. Ceramic filters replaced this type of tuned filter, offering a tuning free product that had excellent filter characteristics at a low cost. Murata's kHz ceramic IF filters are fundamentally ladder filters. You will see later that MHz filters are not ladder filters, but rather are monolithic in construction (multiple elements on one piece of ceramic). A ladder filter uses series and parallel resonant elements (or resonators) to achieve a particular filtering characteristic (Figure 35).
Input
Series Element
Series Element
Output
Parallel Element
Parallel Element
Figure 35: Connection Diagram of Resonate elements in kHz Filter
The more series and parallel elements in a ladder filter, the steeper the sides of the passband and the greater the ability of the filter to reject or attenuate the frequencies not in the pass-band of the filter.
How Does It Work
It has been mentioned that the filter uses resonators in a ladder configuration, but it can be hard to understand how a ceramic resonator may be used to construct a filter. To simplify the explanation, we will examine the operation of a two-element ladder filter (Figure 36).
Input
Series Element
Output
Parallel Element
Figure 36: Two Element kHz Filter Example
To begin the discussion, one must have a basic understanding of the electrical characteristics of a resonator, specifically its impedance response. A ceramic resonator has the impedance response shown in Figure 37.
Page 36
PZT Application Manual
Impedance |Z| ()
fr
fa
Frequency
Figure 37: Impedance Plot of Ceramic Resonator
As can be seen from Figure 37, a ceramic resonator has two key impedance parameters: fr and fa. fr is the frequency where the resonator's impedance is the lowest and fa is the frequency where the resonator's impedance is the highest. For a normal resonator, the resonator will oscillate somewhere between these two frequencies, or, in other words, between the impedance minimum and maximum. By combining two resonators in a ladder configuration where one resonator is the series element and one resonator is the parallel element of the filter, a band pass filter type of performance can be achieved. Figure 38 illustrates this.
Parallel Element
Series Element
Impedance
Fr
Fa
6dB
Attenuation
Frequency
Figure 38: Resonators Combined to Achieve Bandpass Filter
As shown in Figure 38, the impedances at fr and fa of the parallel and series resonant elements are used to make the band pass characteristic. The impedance of the parallel element at fr is used to make the band pass filter's attenuation point below the pass band. The impedances at fa of the parallel element and at fr of the series element make the band itself. Finally, the impedance at fa of the series element is used to make the band pass filter's attenuation point above the pass band. By using these impedances, the basic band pass characteristics are achieved. By increasing the number of elements, the selectivity and stop-band attenuation are improved. At any frequency below fr and above fa, resonators are electrically equivalent to capacitors. To attenuate frequencies in the stopband of the filter, the shunt capacitance of the parallel resonant elements must be much larger than that of the series resonant elements.
PZT Application Manual
Page 37
Parts
The following series of tables will cover the kHz filter part numbering structure, show the difference between the various kHz filter series, and provide a chart of electrical characteristics for each series Figure 39 shows basic kHz filter part numbering structure. Table 6 shows current available kHz filter series and describes each series generally. Some older series are shown for reference purposes, so all series with an asterisk (*) are not available for new designs and may be obsolete.
CFWS 455 C Y
Series
See list of available kHz series
Center Frequency
Bandwidth B = + 15kHz C= + 12.5kHz D= + 10kHz E = + 7.5kHz F = + 6kHz G= + 4.5kHz H= + 3kHz I = + 2kHz
Type Blank = Non GDT
Y = GDT
Figure 39: kHz Filter Part Numbering System
kHz Filter Series Type
Description
GDT Type
CFYM Series*
Miniature 2 element IF filter
N
CFU Series*
4 element IF filter
N
CFUM Series
Miniature version of CFU series
N
CFWM Series
Miniature version of CFW series
N
CFWS Series
6 element IF filter. Lower profile than the CFW series Replaces CFW series filter.
N
CFV Series*
7 element IF filter
N
CFVS Series*
7 element low profile version of the CFV series
N
CFVM Series*
Miniature version of the CFV series
N
CFZM Series*
Miniature high performance 9 element IF filter
N
CFUS...Y Series*
4 element GDT IF filter. Replaces SFG series
Y
CFUM...Y Series
Miniature version of CFUS...Y series. Replaces SFGM series
Y
CFWS...Y Series
6 element GDT IF filter. Replaces SFH series
Y
CFWM...Y Series
Miniature version of CFWS...Y series. Replaces SFHM series Y
SFPC Series
Low cost (5mm) 4 element SMD IF filter
N
CFUCG Series
Low Profile (4mm) 4 element SMD IF filter. Typically narrower bandwidths only.
N
CFUCG...X Series
Low Profile (4mm) 4 element mid-GDT SMD IF filter. Typically narrower bandwidths only.
Y
SFGCG Series
Low Profile (4mm) 4 element GDT SMD IF filter. Typically wider bandwidths only.
Y
Metal or Plastic Case
P P P P P P P P P P
P
P
P P P
P
P
SMD
N N N N N N N N N N
N
N
N Y Y
Y
Y
Promoted In US N Y Y Y Y N N Y Y Y
Y
Y
Y Y Y
Y
Y
Table 6. kHz Filter Description (all SMD parts are on tape and part numbers end in "-TC")
Page 38
PZT Application Manual
CFUCJ Series*
Low Profile (4mm) 4 element SMD IF filter. Typically narrower bandwidths only. "Y" version (GDT) possible for wider bandwidths.
Y/N
P
Y
CFUCH Series
Low Profile (3mm) 4 element SMD IF filter. Typically narrower bandwidths only. "Y" version (GDT) possible for wider bandwidths.
Y/N
P
Y
CFWC Series
Low Profile (3mm) 6 element SMD IF filter. Typically narrower bandwidths only. "Y" version (GDT) possible for wider bandwidths.
Y/N
P
Y
CFZC Series
Low Profile (3mm) 8 element SMD IF filter. Typically narrower bandwidths only. "Y" version (GDT) possible for wider bandwidths.
Y/N
P
Y
CFUXC Series
Low Profile (2mm) 4 element SMD IF filter.
Y
P
Y
CFJ Series*
11 element IF filter. 455kHz version only.
N
M
N
CFG Series*
A miniature 7 element filter with performance like CFM Series. 455kHz version only.
N
M
N
CFX Series*
A miniature 9 element filter with performance like CFL Series. 455kHz version only.
N
M
N
CFL Series*
A miniature 9 element filter with performance like CFR Series. 455kHz version only.
N
M
N
CFK Series*
A miniature 11 element filter with performance like CFS series. 455kHz version only
N
M
N
CFM Series*
9 element filter. 455kHz version only
N
M
N
CFR Series*
11 element filter. 455kHz version only.
N
M
N
CFS Series*
Highest selectivity: 15 element filter. 455kHz version only.
N
M
N
CFKR Series*
Highly selective GDT 11 element filter. For narrower bandwidths. 455kHz version only.
Y
M
N
CFL...G series*
Highly selective GDT 9 element filter. For wider bandwidths. 455kHz version only.
Y
M
N
Table 6. kHz Filter Description (all SMD parts are on tape and part numbers end in "-TC")
Limited
Limited
Limited
Limited Y Y Y
Y
Y
Y Y Y Y Y
Y
Table 7 provides a more detailed performance description for the common kHz filter parts in each series.
Part Number (450kHz also
available)
CFYM Series* CFYM455B CFYM455C CFYM455D CFYM455E CFYM455F
Nominal Center Frequency (kHz)
455 455 455 455 455
CFU Series* CFU455B2 455+2 CFU455C2 455+2 CFU455D2 455+1.5 CFU455E2 455+1.5 CFU455F2 455+1.5 CFU455G2 455+1 CFU455H2 455+1 CFU455I2 455+1 CFU455HT 455+1 CFU455IT 455+1
3dB Bandwidth (kHz)
min.
--------------------------------------------------------
---------------------------------------------------------------------------------------------------------------
6dB Band- 20 dB Band-
width (kHz) width (kHz)
min.
max.
+ 15 + 12.5 + 10 + 7.5
+ 6
+ 30 + 24 + 20 + 15 + 12.5
40 dB Bandwidth (kHz)
max.
+ 15 + 12.5 + 10 + 7.5
+ 6 + 4.5 + 3 + 2 + 3 + 2
+ 30 + 24 + 20 + 15 + 12.5 + 10 + 9 + 7.5 + 9 + 7.5
Attenuation 455+100kHz
(dB) min.
11 12 12 12 12
27 27 27 27 27 25 25 25 35 35
Insertion Input/ output Loss (dB) Impedance ()
4
1,500
4
1,500
4
1,500
4
1,500
4
2,000
Ripple (dB) max.
4
1,500 3 (455+10)
4
1,500 4 (455+8)
4
1,500 2 (455+7)
6
1,500 1.5 (455+5)
6
2,000 1.5 (455+4)
6
2,000 1.5 (455+3)
6
2,000 2 (455+2)
6
2,000 2 (455+1.5)
6
2,000 2 (455+2)
6
2,000 2 (455+1.5)
Table 7. kHz Filters (455kHz shown, but 450kHz version also available for most filters)
PZT Application Manual
Page 39
CFUM Series CFUM455B CFUM455C CFUM455D CFUM455E CFUM455F CFUM455G CFUM455H CFUM455I CFWS Series CFWS455B CFWS455C CFWS455D CFWS455E CFWS455F CFWS455G CFWS455HT CFWS455IT CFWM Series CFWM455B CFWM455C CFWM455D CFWM455E CFWM455F CFWM455G CFWM455H CFWM455I CFV Series*
CFV455B CFV455C CFV455D CFV455E CFV455E10 CFV455F CFV455G CFV455H CFV455I
CFVS Series* CFVS455D CFVS455E CFVS455E10 CFVS455F CFVS455G CFVS455H CFVM Series* CFVM455B CFVM455C CFVM455D CFVM455E
455 ------------ + 15
+ 30
27
455 ------------ + 12.5
+ 24
27
455 ------------ + 10
+ 20
27
455 ------------ + 7.5
+ 15
27
455 ------------
+ 6
+ 12.5
27
455 ------------ + 4.5
+ 10
25
455 ------------
+ 3
+ 9
35
455 ------------
+ 2
+ 7.5
35
4
1,500 ------------
4
1,500 ------------
4
1,500 2 (455+7)
6
1,500 1.5 (455+5)
6
2,000 1.5 (455+4)
6
2,000 1.5 (455+3)
6
2,000 1.5 (455+2)
7
2,000 2 (455+1.5)
455 ------------ + 15
+ 30
35
455 ------------ + 12.5
+ 24
35
455 ------------ + 10
+ 20
35
455 ------------ + 7.5
+ 15
35
455 ------------
+ 6
+ 12.5
35
455 ------------ + 4.5
+ 10
35
455 ------------
+ 3
+ 9
60
455 ------------
+ 2
+ 7.5
60
455 ------------ + 15
+ 30
35
455 ------------ + 12.5
+ 24
35
455 ------------ + 10
+ 20
35
455 ------------ + 7.5
+ 15
35
455 ------------
+ 6
+ 12.5
35
455 ------------ + 4.5
+ 10
35
455 ------------
+ 3
+ 9
55
455 ------------
+ 2
+ 7.5
55
60 dB Bandwidth (kHz)
max.
455
+ 10
+ 15
+ 25
50
455
+ 9
+ 13
+ 23
50
455
+ 7
+ 10
+ 20
50
455
+ 5.5
+ 8
+ 16
50
455
+ 5
+ 7
+ 12.5
50
455
+ 4.2
+ 6
+ 12
50
455 ------------
+ 4
+ 10
50
455 ------------
+ 3
+ 7.5
50
455 ------------
+ 2
+ 5
50
4
1,500 3 (455+10)
4
1,500 3 (455+8)
4
1,500 3 (455+7)
6
1,500 3 (455+5)
6
2,000 3 (455+4)
6
2,000 2 (455+3)
6
2,000 2 (455+2)
6
2,000 2 (455+1.5)
4
1,500 3 (455+10)
4
1,500 3 (455+8)
4
1,500 3 (455+7)
6
1,500 3 (455+5)
6
2,000 3 (455+4)
6
2,000 2 (455+3)
6
2,000 2 (455+2)
7
2,000 2 (455+1.5)
Spurious 0.1-1 MHz (dB) min.
4
1,000
3
25
4
1,000
3
25
4
1,500
3
25
6
1,500
3
25
6
1,500
3
25
6
1,500
3
25
6
1,500
3
25
6
1,500
3
25
6
2,000
3
25
455
+ 7
+ 10
+ 20
50
455
+ 5.5
+ 8
+ 16
50
455
+ 5
+ 7
+ 12.5
50
455
+ 4.2
+ 6
+ 12
50
455 ------------
+ 4
+ 10
50
455 ------------
+ 3
+ 7.5
50
4
1,500
3
25
6
1,500
3
25
6
1,500
3
25
6
1,500
3
25
6
1,500
3
25
6
1,500
3
25
455
+ 10
+ 15
+ 25
50
455
+ 9
+ 13
+ 23
50
455
+ 7
+ 10
+ 20
50
455
+ 5.5
+ 8
+ 16
50
4
1,000
3
25
4
1,000
3
25
4
1,500
3
25
6
1,500
3
25
Table 7. kHz Filters (455kHz shown, but 450kHz version also available for most filters)
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PZT Application Manual
CFVM455E10 455
+ 5
+ 7
+ 12.5
50
CFVM455F 455
+ 4.2
+ 6
+ 12
50
CFVM455G 455 ------------
+ 4
+ 10
50
CFVM455H 455 ------------
+ 3
+ 7.5
50
CFZM Series*
70 dB Bandwidth (kHz)
max.
CFZM455B 455
+ 10
+ 15
+ 25
70
CFZM455C 455
+ 9
+ 13
+ 23
70
CFZM455D 455
+ 7
+ 10
+ 20
70
CFZM455E 455
+ 5.5
+ 8
+ 16
70
CFZM455E10 455
+ 5
+ 7
+ 12.5
70
CFZM455F 455
+ 4.2
+ 6
+ 12
70
CFZM455G 455 ------------
+ 4
+ 10
70
CFZM455H 455 ------------
+ 3
+ 7.5
70
CFUS...Y Series*
40 dB Bandwidth (kHz)
max.
CFUS455BY 455+1.5 ------------ + 15
+ 35
25
CFUS455CY 455+1.5 ------------ + 12.5
+ 30
25
CFUS455DY 455+1 ------------ + 10
+ 25
23
CFUS455EY 455+1 ------------ + 7.5
+ 20
23
CFUS455FY 455+1 ------------
+ 6
+ 17.5
23
CFUS455GY 455+1 ------------ + 4.5
+ 15
23
CFUM...Y
Series
CFUM455BY 455+1.5 ------------ + 15
+ 35
25
CFUM455CY 455+1.5 ------------ + 12.5
+ 30
25
CFUM455DY 455+1 ------------ + 10
+ 25
23
CFUM455EY 455+1 ------------ + 7.5
+ 20
23
CFUM455FY 455+1 ------------
+ 6
+ 17.5
23
CFUM455GY 455+1 ------------ + 4.5
+ 15
20
CFWS...Y Series
50 dB Bandwidth (kHz)
max.
CFWS455BY 455+1.5 ------------ + 15
+ 35
35
CFWS455CY 455+1.5 ------------ + 12.5
+ 30
35
CFWS455DY 455+1 ------------ + 10
+ 25
35
CFWS455EY 455+1 ------------ + 7.5
+ 20
35
CFWS455FY 455+1 ------------
+ 6
+ 17.5
35
CFWS455GY 455+1 ------------ + 4.5
+ 15
35
CFUXC Series
CFUXC450A1 450 ------------ + 17.5
+ 55
50
00H
CFUXC450B1 450 ------------ + 15
+ 50
47
00H
CFUXC450C1 450 + 9 to + 12 ------------ + 35
47
00H
CFWM...Y
Series
CFWM455BY 455+1.5 ------------ + 15
+ 35
35
CFWM455CY 455+1.5 ------------ + 12.5
+ 30
35
CFWM455DY 455+1 ------------ + 10
+ 25
35
CFWM455EY 455+1 ------------ + 7.5
+ 20
35
CFWM455FY 455+1 ------------
+ 6
+ 17.5
35
CFWM455GY 455+1 ------------ + 4.5
+ 15
35
6
1,500
3
25
6
1,500
3
25
6
1,500
3
25
6
1,500
3
25
4
1,000
4
1,000
4
1,500
6
1,500
6
1,500
6
1,500
6
1,500
7
1,500
5
1,500
6
1,500
7
1,500
8
1,500
9
2,000
10
2,000
3
40
3
40
3
40
3
40
3
40
3
50
3
50
3
50
G.D.T. Deviation Typical (µS)
1
------------ (15) (+ 10kHz)
1
------------ (15) (+ 8kHz)
1
------------ (20) (+ 7kHz)
1
------------ (20) (+ 5kHz)
1
------------ (20) (+ 4kHz)
1
------------ (20) (+ 3kHz)
5
1,500 ------------ ------------ (15) (+ 10kHz)
6
1,500 ------------ ------------ (15) (+ 8kHz)
7
1,500 ------------ ------------ (20) (+ 7kHz)
8
1,500 ------------ ------------ (20) (+ 5kHz)
9
2,000 ------------ ------------ (20) (+ 4kHz)
10
2,000 ------------ ------------ (20) (+ 3kHz)
6
1,500 ------------ ------------ (30) (+ 10kHz)
7
1,500 ------------ ------------ (30) (+ 8kHz)
8
1,500 ------------ ------------ (30) (+ 7kHz)
9
1,500 ------------ ------------ (30) (+ 5kHz)
10
2,000 ------------ ------------ (40) (+ 4kHz)
13
2,000 ------------ ------------ (40) (+ 3kHz)
5
2,000
0.5
6
2,000
0.5
6
2,000
0.5
40 (15) (+ 12kHz)
40 (15) (+ 10kHz)
40
(27) (+
10.5kHz)
6
1,500 ------------ ------------ (30) (+ 10kHz)
7
1,500 ------------ ------------ (30) (+ 8kHz)
8
1,500 ------------ ------------ (30) (+ 7kHz)
9
1,500 ------------ ------------ (30) (+ 5kHz)
10
2,000 ------------ ------------ (40) (+ 4kHz)
13
2,000 ------------ ------------ (40) (+ 3kHz)
Table 7. kHz Filters (455kHz shown, but 450kHz version also available for most filters)
PZT Application Manual
Page 41
SFPC Series
40 dB Bandwidth (kHz)
max.
SFPC455D 455+1.5 ------------ + 10
+ 20
27
4
SFPC455E 455+1.5 ------------ + 7.5
+ 15
27
6
SFPC455F 455+1.5 ------------
+ 6
+ 12.5
27
6
SFPC455G 455+1 ------------ + 4.5
+ 10
25
6
SFPC455H 455+1 ------------
+ 3
+ 9
25
6
CFUCG
Series
CFUCG455D 455+1.5 ------------ + 10
+ 20
27
4
CFUCG455E 455+1.5 ------------ + 7.5
+ 15
27
6
CFUCG455F 455+1.5 ------------
+ 6
+ 12.5
27
6
CFUCG455G 455+1 ------------ + 4.5
+ 10
25
6
CFUCG...X
Series
CFUCG455EX 455+1.5 ------------ + 7.5
+ 17.5
27
6
CFUCG455FX 455+1.5 ------------
+ 6
+ 15
27
6
CFUCG455GX 455+1 ------------ + 4.5
+ 12.5
25
6
CFUCG455HX 455+1 ------------
+ 3
+ 10
25
7
SFGCG
Series
SFGCG455AX 455+2 ------------ + 17.5
+ 40
25
4
SFGCG455BX 455+1.5 ------------ + 15
+ 35
25
5
SFGCG455CX 455+1.5 ------------ + 12.5
+ 30
25
6
SFGCG455DX 455+1 ------------ + 10
+ 25
23
7
SFGCG455EX 455+1 ------------ + 7.5
+ 20
23
8
CFWC Series
50 dB Bandwidth (kHz)
max.
CFWC455C 455 ------------ + 12.5
+ 24
45
4
CFWC455D 455 ------------ + 10
+ 20
50
4
CFWC455E 455 ------------ + 7.5
+ 15
50
6
CFWC455F 455 ------------
+ 6
+ 12.5
50
6
CFWC455G 455 ------------ + 4.5
+ 11
50
6
CFJ Series*
60 dB Bandwidth (kHz)
max.
CFJ455
455 ------------ 2.4 (Total) 4.5 (Total) ------------
6
CFJ455
455 ------------ +1.1 - +1.3 4.5 (Total) ------------
7
CFJ455
455 ------------ 1.0 (Total) 3.0 (Total)
60
8
CFG Series*
CFG455B
455
+ 10
+ 15
+ 25
50
4
CFG455C
455
+ 9
+ 13
+ 23
50
4
CFG455D
455
+ 7
+ 10
+ 20
50
4
CFG455E
455
+ 5.5
+ 8
+ 16
50
6
CFG455E10 455
+ 5
+ 7
+ 12.5
50
6
CFG455F
455
+ 4.2
+ 6
+ 12
50
6
CFG455G
455 ------------
+ 4
+ 10
50
6
CFG455H
455 ------------
+ 3
+ 7.5
50
6
CFG455I
455 ------------
+ 2
+ 5
50
6
CFG455J
455 ------------ + 1.5
+ 4.5
50
8
CFX Series*
1,500 1,500 1,500 1,500 2,000
1,500 1,500 1,500 1,500
1,500 1,500 1,500 1,500
1,000 1,000 1,000 1,500 1,500
2
------------ ------------
1.5 ------------ ------------
1.5 ------------ ------------
1.5 ------------ ------------
1.5 ------------ ------------
2
------------ ------------
1.5 ------------ ------------
1.5 ------------ ------------
1.5 ------------ ------------
G.D.T. Deviation (µS) max.
1
------------
25
1
------------
25
1
------------
25
1
------------
25
1
------------
15
1
------------
15
1
------------
15
1
------------
20
1
------------
20
1,500 1,500 1,500 1,500 1,500
3 (455+8) 3 (455+7) 3 (455+5) 3 (455+4) 2 (455+3)
--------------------------------------------------------
--------------------------------------------------------
2,000
2,000
2,000
1,000 1,000 1,000 1,500 1,500 1,500 1,500 1,500 2,000 2,000
2
60 (40 at ------------
600 - 700
kHz)
2
60 (40 at ------------
600 - 700
kHz)
1.5 ------------ ------------
3
25
------------
3
25
------------
3
25
------------
3
25
------------
3
25
------------
3
25
------------
3
25
------------
3
25
------------
3
25
------------
3
25
------------
Table 7. kHz Filters (455kHz shown, but 450kHz version also available for most filters)
Page 42
PZT Application Manual
CFX455B CFX455C CFX455D CFX455E CFX455E10 CFX455F CFX455G CFX455H CFX455I CFX455J CFL Series* CFL455B CFL455C CFL455D CFL455E CFL455E10 CFL455F CFL455G CFL455H CFL455I CFK Series* CFK455B CFK455C CFK455D CFK455E CFK455E10 CFK455F CFK455G CFK455H CFK455I CFK455J CFM Series* CFM455A CFM455B CFM455C CFM455D CFM455E CFM455F CFM455G CFM455H CFM455I CFR Series* CFR455A CFR455B CFR455C CFR455D CFR455E CFR455F CFR455G CFR455H CFR455I CFR455J CFS Series* CFS455
455
+ 10
+ 15
+ 25
70
455
+ 9
+ 13
+ 23
70
455
+ 7
+ 10
+ 20
70
455
+ 5.5
+ 8
+ 16
70
455
+ 5
+ 7
+ 12.5
70
455
+ 4.2
+ 6
+ 12
70
455 ------------
+ 4
+ 10
70
455 ------------
+ 3
+ 7.5
70
455 ------------
+ 2
+ 5
70
455 ------------ + 1.5
+ 4.5
70
4
1,000
3
40
4
1,000
3
40
4
1,500
3
40
6
1,500
3
40
6
1,500
3
40
6
1,500
3
50
6
1,500
3
50
7
1,500
3
50
8
2,000
3
50
8
2,000
3
50
455
+ 10
+ 15
+ 25
60
455
+ 9
+ 13
+ 23
60
455
+ 7
+ 10
+ 20
60
455
+ 5.5
+ 8
+ 16
60
455
+ 5
+ 7
+ 12.5
60
455
+ 4.2
+ 6
+ 12
60
455 ------------
+ 4
+ 10
60
455 ------------
+ 3
+ 7.5
60
455 ------------
+ 2
+ 5
60
4
1,000
3
40
4
1,000
3
40
4
1,500
3
40
6
1,500
3
40
6
1,500
3
40
6
1,500
3
40
6
1,500
3
40
7
1,500
3
40
8
2,000
3
40
455
+ 10
+ 15
+ 25
80
455
+ 9
+ 13
+ 23
80
455
+ 7
+ 10
+ 20
80
455
+ 5.5
+ 8
+ 16
80
455
+ 5
+ 7.5
+ 12.5
80
455
+ 4.2
+ 6
+ 12
80
455 ------------
+ 4
+ 10
80
455 ------------
+ 3
+ 7.5
80
455 ------------
+ 2
+ 5
70
455 ------------ + 1.5
+ 4.5
70
4
1,000
3
50
4
1,000
3
50
4
1,500
3
50
6
1,500
3
50
6
1,500
3
50
6
2,000
3
50
6
2,000
3
50
7
2,000
3
50
8
2,000
3
50
8
2,000
3
50
455
+ 13
+ 17.5
+ 30
50
455
+ 10
+ 15
+ 25
50
455
+ 9
+ 13
+ 23
50
455
+ 7
+ 10
+ 20
50
455
+ 5.5
+ 8
+ 16
45
455
+ 4.2
+ 6
+ 12
45
455 ------------
+ 4
+ 10
45
455 ------------
+ 3
+ 7.5
45
455 ------------
+ 2
+ 5
45
3
1,000
3
30
3
1,000
3
30
3
1,000
3
30
3
1,500
3
30
5
1,500
3
30
6
2,000
3
30
6
2,000
3
30
6
2,000
3
30
7
2,000
3
30
455
+ 13
+ 17.5
+ 30
60
455
+ 10
+ 15
+ 25
60
455
+ 9
+ 13
+ 23
60
455
+ 7
+ 10
+ 20
60
455
+ 5.5
+ 8
+ 16
55
455
+ 4.2
+ 6
+ 12
55
455 ------------
+ 4
+ 10
55
455 ------------
+ 3
+ 7.5
55
455 ------------
+ 2
+ 5
55
455 ------------ + 1.5
+ 4.5
55
4
1,000
3
40
4
1,000
3
40
4
1,000
3
40
4
1,500
3
40
6
1,500
3
40
6
2,000
3
40
6
2,000
3
40
7
2,000
3
40
8
2,000
3
40
8
2,000
3
40
455
+ 13
+ 17.5
+ 30
70
4
1,500
3
50
Table 7. kHz Filters (455kHz shown, but 450kHz version also available for most filters)
---------------------------------------------------------------------------------------------------------------
----------------------------------------------------------------------------------------------------
---------------------------------------------------------------------------------------------------------------
----------------------------------------------------------------------------------------------------
---------------------------------------------------------------------------------------------------------------
------------
PZT Application Manual
Page 43
CFS455
455
+ 10
+ 15
+ 25
70
4
CFS455
455
+ 9
+ 13
+ 23
70
4
CFS455
455
+ 7
+ 10
+ 20
70
4
CFS455
455
+ 5.5
+ 8
+ 16
70
6
CFS455
455
+ 5
+ 7
+ 12.5
70
6
CFS455
455
+ 4.2
+ 6
+ 12
70
6
CFS455
455 ------------
+ 4
+ 10
70
6
CFS455
455 ------------
+ 3
+ 7.5
70
7
CFS455
455 ------------
+ 2
+ 5
70
8
CFS455
455 ------------ + 1.5
+ 4.5
60
8
CFKR Series*
Stop Bandwidth (kHz)
max.
CFRK455E1 455
+ 5.8 ------------ + 17 (70dB
70
4
BW)
CFRK455G1 455
+ 3
+ 4
+ 11.5
70
6
(60dB BW)
CFRK455H3 455 ------------ + 3.5
+ 11.2
60
6
(60dB BW)
CFL...G Series*
60 dB Bandwidth (kHz)
max.
CFL455AG2 455+ 1.0 ------------ + 17.5 - 48dBmin. 65 (+ 40kHz) 7.5 +19.5 (+ 29kHz)
CFL455BG2 455
+ 10.5
+ 13.5
+ 27.5
60
10
Nominal
CFL455CG1 455
+ 9.5
+ 12
+ 25.5
60
10
Nominal
CFL455DG2 455
+ 7
+ 9
+ 21
60
11
Nominal
CFL455EG1 455
+ 5
+ 7
+ 18
60
13
Nominal
1,500
3
1,500
3
1,500
3
1,500
3
1,500
3
2,000
3
2,000
3
2,000
3
2,000
3
2,000
3
50
------------
50
------------
50
------------
50
------------
50
------------
50
------------
50
------------
50
------------
50
------------
50
------------
1,500 1,500 1,500
------------ ------------ 40 (+ 6kHz) ------------ ------------ 35 (+ 4kHz) ------------ ------------ 25 (+ 3.5kHz)
1,000 1,000 1,000 1,000 1,500
--------------------------------------------------------
40 40 (+ 15kHz)
30
25 (+
10.5kHz)
30 35 (+ 9.5kHz)
30
35 (+ 7kHz)
30
30 (+ 5kHz)
Table 7. kHz Filters (455kHz shown, but 450kHz version also available for most filters)
Page 44
PZT Application Manual
Page 45
PZT Application Manual
Figure 40: kHz Filter Selection Chart
Non-GDT
CFWS Series 6 Element [35dB] ,C,D,E, F, G,HT,IT)
CFM Series Metal Case 9 Element [50dB] A,B,C,D,E,F,G,H,I)
CFR Series MEtal Case 1 Element [60dB] ,B,C,D,E,F,G,H,I,J)
CFJ Series Metal Case 1 Element [60dB] (K5,K14,K8)
CFS Series Metal Case 5 Element [70dB] ,B,C,D,E,F,G,H,I,J)
Leaded
START kHz Filters (B,C,...) = Available Bandwidths [dB] = Typical Attenuation
Surface Mount
Miniature
CFUM Series 4 Element [27dB]
(B,C,D,E,F,G,I)
CFWM Series 6 Element [35dB]
(B,C,D,E,F,G,I)
CFVM Series 7 Element [50dB] (B,C,D,E,F,G,H)
CFZM Series 9 Element [70dB] (B,C,D,E,F,G,H)
CFG Series Metal Case 7 Element [50dB] (B,C,D,E,F,G,H,I,J)
CFL Series Metal Case 9 Element [60dB] (B,C,D,E,F,H,I)
CFX Series Metal Case 9 Element [60dB] (B,C,D,E,F,H,I,J)
CFK Series Metal Case 11 Element [80dB] (B,C,D,E,F,G,H,I,J)
GDT
CFUS...Y Series 4 Element [25dB]
(B,C,D,E,F,G)
CFWS...Y Series 6 Element [35dB] (A,B,C,D,E,F,G)
CFL...G Series Metal Case
9 Element [60dB] (A,B,C,D,E)
CFKR Series Metal Case 11 Element [70dB] (D,E,F,G,H)
Miniature
CFUM...Y Series 4 Element [25dB]
(B,C,D,E,F,G)
CFWM...Y Series 6 Element [35dB]
(B,C,D,E,F,G)
Non-GDT
SFPC Series 4 Element [27dB]
Height = 5mm (D,E,F,G,H)
CFUCG Series 4 Element [27dB]
Height = 4mm (D,E,F,G,H)
CFWC Series 6 Element [46dB]
Height = 3mm (Limited)
Metal Can kHz Filter Bandwidths (6dB)
Letter A B C D E F G H I J
BW +17.5kHz +15kHz +13kHz +10kHz +8kHz +6kHz +4kHz +3kHz +2kHz +1.5kHz
K5
2.4kHz total
K14
+1.1~+1.3kHz
K8
1.0kHz total
BG5 CG1 DG2 EG1
+13.5kHz +12.0kHz +9.0kHz +7.0kHz
CFZC Series 8 Element [55dB]
Height = 3mm (Limited)
CFWS filters ending in "T" are high attenuation
type filters.
Standard kHz Filter Bandwidths (6dB)
Letter B C D E F G H I
BW +15kHz +12.5kHz +10kHz +7.5kHz +6kHz +4.5kHz +3kHz +2kHz
GDT
SFGCG Series 4 Element [25dB]
Height = 4mm (A,B,C,D,E)
CFWC...Y Series 6 Element [42dB]
Height = 3mm (Limited)
CFZC...Y Series 8 Element [52dB]
Height = 3mm (Limited)
CFUXC Series 4 Element [50dB]
Height = 2mm (Limited)
Mid-GDT
CFUCG...X Series 4 Element [27dB]
Height = 4mm (E,F,G,H)
MHz Filters
Introduction
Today, most FM radio designs use 10.7MHz IF filters. The characteristics of these filters help determine the performance characteristics of the radio it is used in. Besides providing low cost filtering, ceramic10.7MHz IF filters provide high selectivity, excellent temperature and environmental characteristics, optimal GDT performance, and a pass-band that is symmetrical around the center frequency. Such filters can provide all this while being packaged in a very compact leaded or SMD package. Murata also makes MHz filters for TV sound IF filtering. These filters operate similar to 10.7MHz filters, but cover the 3.58 to 7.0MHz range. This range covers the common Sound IF freqeuncies for NTSC and PAL based systems.
How Does It Work
Ceramic 10.7 MHz IF filters do not use a ladder construction like the kHz filters. The MHz filters are monolithic (one or more elements on a single substrate) in construction, similar to ceramic resonators. These filters utilize the trapped energy of the thickness longitudinal vibration mode in a single ceramic substrate to achieve the filtering effect, unlike the kHz filters that require a number of elements to achieve the filtering effect. You may ask why Murata does not make the kHz filter like the MHz filter or the MHz like the kHz. The answer to this is that the frequency of operation determines which vibration mode may be used to achieve the filtering effect. The area vibration mode used by the kHz filters does not work in the MHz range and the thickness longitudinal vibration mode used by the MHz filters does not work in the kHz range. The thickness longitudinal vibration mode is used in ceramic resonators as well as MHz filters. We will start the explanation of how these filters work by explaining how a resonator works and then progress to the more complex design of the filter.
Substrate
t
Electrode
Figure 41: Basic Construction of Thickness Vibration Mode Resonator
Figure 41 shows the basic construction of a thickness expansion vibration mode resonator. A thin ceramic substrate has metal electrodes on both the top and bottom, directly over each other. Vibration of the resonator occurs only in the ceramic between the electrodes. The thickness of the ceramic substrate, shown as t in Figure 41, determines the resonant frequency of the resonator. While this design results in a very good ceramic resonator, other modifications must be made in order to make it a good filter. Here, we come upon the idea of multi-coupling mode. In multi-coupling mode, the top electrode is divided into two separate electrodes. This new electrode allows different frequency resonances to become trapped between the electrodes (two vibration modes instead of one). The phase relationship between these two vibration modes is different as well.
Page 46
PZT Application Manual
Symmetrical Mode
IN
OUT
GND
Anti-Symmetrical Mode
Figure 42: MHz Filter Vibration Mode
Figure 42 shows the two vibration modes resulting from the splitting of the electrode, the symmetrical and anti-symmetrical vibration modes. Since there are now two vibration modes, it is the same as having two elements in the filter.
Symmetrical Mode X
Anti-symmetrical Mode X
Resonant Frequency
X Anti-resonant Frequency
Output Level
Frequency
Figure 43: How the Filter Achives Bandpass Filter Effect
Figure 43 shows how the symmetrical and anti-symmetrical modes are utilized to create the filter response. Each mode has its own resonant and anti-resonant frequency, like two separate elements. By cascading two of these split electrode patterns we produce Murata's SFE10.7 filters. Murata's SFT10.7 filters use three of these split electrode patterns on a single substrate to make an even higher selectivity filter.
Parts
The following tables show the MHz part numbering system and the filters offered by Murata. Figure 44 below describes the basic 10.7 MHz part number structure.
PZT Application Manual
Page 47
SFE 10.7 MA5 H - A
Series
See list of available MHz series
Center Frequency Indicates
(MHz)
Electrical
Specification
Tolerance of Center Frequency
Rank of Center Frequency
No Code = + 30kHz SeeTable 8 for list of
H= + 25kHz
possible letters
K = + 20kHz
Center frequency ranks
K and H option not other than "A" not
available for every available for all parts
filter
Figure 44: MHz Part Numbering System
Table 8 indicates the possible center frequency rank for the 10.7MHz filters. While all ranks are possible, all ranks have not been design up each 10.7MHz part number. Please consult with Murata for rank availability for specific 10.7MHz part number.
Code
D B A C E Z M
30kHz Step Tolerance Code Equal To
"No Code"
25 kHz Step Tolerance Code Equal To "H"
10.64MHz+30kHz
10.64MHz+25kHz
10.67MHz+30kHz
10.67MHz+25kHz
10.70MHz+30kHz
10.70MHz+25kHz
10.73MHz+30kHz
10.73MHz+25kHz
10.76MHz+30kHz
10.76MHz+25kHz
Combination Of: A,B,C,D,E
Combination Of: A,B,C
Table 8. Rank of Center Frequency
Color Code
Black Blue Red Orange White
Table 9 describes each commonly available 10.7MHz and Sound IF (SFSH) filter series. Some older series are listed for reference only so any part with an asterisk (*) by it is no longer available for new designs.
MHz Filter Series Type
SFE A10 SFE B10 SFE C10 SFE MX SFE MA8 SFE ML SFE MA19 SFE MTE SFE MVE SFE MFP
Description
GDT Type
Low loss and high selectivity
N
High attenuation
N
Thin and low profile. Same performance.
N
Controlled G.D.T filter
Y
Controlled G.D.T filter
Y
Controlled G.D.T filter
Y
Wide bandwidth filter.
N
Narrow bandwidth
N
Narrow bandwidth
N
Narrow bandwidth
N
Table 9. MHz Filter Series Description
SMD
N N N N N N N N N N
Page 48
PZT Application Manual
SFT
Single substrate 3 section filter. High selectivity and spurious suppression.
N
N
SFECV
Surface mount IF filter
N
Y
SFECS
Miniature version of SFECV
N
Y
CFEC*
Surface mount IF filter
N
Y
KMFC545
Super wide bandwidth filter
N
N
CFECV
GDT controlled version of SFECV
Y
Y
CFECS
Miniature version of CFECV
Y
Y
SFSH*
TV IF filter, 3.58 6.5MHz
N
N
SFSRA
TV IF filter, 3.58 6.5MHz
N
N
SFSCC Surface Mount TV IF filter, 3.58 6.5MHz
N
Y
Table 9. MHz Filter Series Description
PZT Application Manual
Page 49
Table 10 provides general electrical specification for common 10.7MHz and Sound IF (SFSH) filters. Please note that values in parenthases are typical values.
Part Number
SFE Series SFE10.7MA5-A SFE10.7MS2-A SFE10.7MS3-A SFE10.7MA5A10-A SFE10.7MS2A10-A SFE10.7MS3A10-A SFE10.7MJA10-A SFE10.7MA5B10-A SFE10.7MS2B10-A SFE10.7MS3B10-A SFE10.7MA5C10-A SFE10.7MS2C10-A SFE10.7MS3C10-A SFE10.7MJC10-A SFE10.7MHC10-A SFE10.7MX-A
SFE10.7MX2-A
SFE10.7MZ1-A SFE10.7MZ2-A
Nominal Center Frequency (MHz)
10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7 10.7
10.7
10.7 10.7
3dB Bandwidth (kHz) min.
20 dB Bandwidth (kHz) max.
Insertion Loss (dB)
Input/ output Impedance
Ripple (dB) max.
280+50 650 (520) 6 (4)
330
230+50 570 (420) 6 (4)
330
180+40 520 (380) 7 (4.5)
330
280+50 590 (480) 2.5 + 2.0 330
230+40 520 (410) 3.0 + 2.0 330
180+40 470 (370) 3.5 + 1.5 330
150+40 360 (300) 4.5 + 2.0 330
280+50
650 3.0 + 2.0 330
230+50
570 3.0 + 2.0 330
180+40
520 5.0 + 2.0 330
280+50 650 (540) 3.0 + 2.0 330
230+50 570 (470) 3.0 + 2.0 330
180+40 470 (360) 3.5 + 2.0 330
150+40 360 (300) 4.5 + 2.0 330
110+30 350 (260) 7.0 + 2.0 330
250+40 670 (620) 12 (10)
330
220+40
610 (560)
12.5 (10.5)
330
180+30 530 (460) 14 (12.3) 330
150+30 500 (420) 14 (12.6) 330
1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 0 max.
0 max.
0 max. 0 max.
SFE10.7MA8-A
10.7
280+50 650 (520) 6 (4)
330
0.5 max.
SFE10.7MS2G-A
10.7
230+50 600 (420) 7 (4.5)
330
0 max.
SFE10.7MS3G-A
10.7
180+40 520 (380) 7 (5)
330
0 max.
SFE10.7ML-A
10.7
280+50 700 (610) 9 (7)
330
0 max.
SFE10.7MP3-A
10.7
250+50 650 (550) 10 (8)
330
1.0 max.
SFE10.7MM-A
SFE10.7MA19 SFE10.7MA20-A
SFE10.7MA21 SFE10.7MHY-A SFE10.7MTE SFE10.7MVE SFE10.7MFP
SFE10.7MFP1
10.7
10.7 10.7 10.7 10.7 10.7 10.7 10.7
10.7
230+50 600 (510) 11 (9)
330
350 (450) 330 + 50 400 (500) 110+30 +25 (80) +13 (53) +20 (38) Fn +5 min. Fn +35
max.
950 (750) 3 + 2
330
680 (615) 4 + 2
330
950 (750) 3 + 2
330
350 (260) 7 + 2
330
200 (160) 6.5 + 2.5 330
135 (109) 6.0 + 2.0 330
95 (78) 6.0 (3.4) 330
----------
6
600
Table 10. MHz Filters
0 max.
3 1 3 1 1 1 1
----------
Spurious (9-12MHz) (dB) min.
30 (43) 40 (45) 40 (45) 30 (42) 35 (42) 35 (42) 35 (42)
45 45 45 30 (47) 40 (49) 35 (47) 35 (42) 30 (38) 25 (33)
30 (37)
33 (38) 35 (41)
30 (43)
40 (45) 40 (45)
25 (33)
30 (35)
30 (38)
20 (30) 30 (40) 20 (30) 30 (38) 30 (55) 30 (50) 24 (28)
----------
G.D.T. Bandwidth (kHz) min.
---------------------------------------------------------------------------------------------------------------------------------------0.2µS fo + 110kHz
0.15µS fo + 80kHz
0.15µS fo + 60kHz 015µS fo + 50kHz
0.5µS fo + 80 (100)
0.5µS fo + 60 (75) 0.5µS fo + 45 (60)
0.25µS fo + 70 (105)
0.25µS fo + 65 (90)
0.25µS fo + 60 (85)
----------------------------------------------------------------
----------
Page 50
PZT Application Manual
SFT Series
SFT10.7MA5
10.7
SFT10.7MS2
10.7
SFT10.7MS3
10.7
SFECV Series
SFECV10.7MA21S- 10.7
A-TC
SFECV10.7MA19S- 10.7
A-TC
SFECV10.7MA2S-ATC
10.7
SFECV10.7MA5S-ATC
10.7
SFECV10.7MS2S-ATC
10.7
SFECV10.7MS3S-ATC
10.7
SFECV10.7MHS-ATC
10.7
SFECV10.7MJS-ATC
10.7
SFECS Series
SFECS10.7MA5-ATC
10.7
SFECS10.7MS2-ATC
10.7
SFECS10.7MS3-ATC
10.7
CFEC Series*
CFEC10.8MK1-TC 10.8
CFEC10.8MG1-TC 10.8
CFEC10.8ME11-TC 10.8
CFEC10.8MD11-TC
CFECS Series CFECS10.75ME11 CFECS10.75MK1 CFECS14.6ME21 CFECS14.6ME27
CFECV Series
10.8
10.75 10.75 14.6 14.6
280 + 50 230 + 40 180 + 40
40 dB Bandwidth (kHz) max. 700 (630) 650 (580) 550 (500)
6 + 2 6 + 2 8 + 2
400 + 50 ---------- 3.0 + 2
350 + 50 ---------- 3.0 + 2.0
Ripple within 3dB BW (dB)
330
0.5 max.
50 (60)
330
0.5 max.
50 (60)
330
0.5 max.
50 (60)
470
3.0 max.
20
470
3.0 max.
20
----------------------------
----------
----------
330 + 50 ---------- 4 + 2
330
----------
30
280+50 ----------
6
330
----------
30
230+50 ----------
6
330
----------
30
180+40 ----------
7
330
----------
30
150+40 ---------- 5.5 + 2.0 330
----------
30
110+30 ---------- 6.0 + 2.0 330
----------
35
20 dB Bandwidth (kHz) max.
-------------------------------------------------------
280+50
590
3.0 + 2
230+50
510
3.5 + 2
180+40
470
4.5 + 2
+110 to +115
+310
6
+135 to +180
+350
6
+150
+420
5
+170
+450
5
+110
+310
6
+150
+420
5
+150
+500
6
+90
----------
6
330
1.0 max.
30
330
1.0 max.
30
330
1.0 max.
30
(fn +
330
100kHz)
----------
0.5
(fn +
330
100kHz)
----------
0.5
330
(fn + 110kHz) 1
25
600
(fn + 170kHz) 1
25
330
0.5
----------
330
1
25
330
1
----------
330
2
----------
----------
----------
----------
G.D.T. Deviation (µS) max.
(fn + 100kHz) 1.5
(fn + 100kHz) 1.2
(fn + 110kHz) 1.5
(fn + 170kHz) 2.0
1.5 1.5 0.8 1
Table 10. MHz Filters
PZT Application Manual
Page 51
CFECV13.0ME21 CFECV14.6ME21
SFSH Series
SFSH4.5MCB
SFSH5.5MCB
SFSH6.0MCB
SFSH6.5MCB
SFSH4.5MDB
SFSH5.5MDB
SFSH6.0MDB
SFSH6.5MDB
SFSH4.5MEB2
SFSRA Series SFSRA4M50EF00-
B0 SFSRA4M50DF00-
B0 SFSRA5M50DF00-
B0 SFSRA6M00DF00-
B0 SFSRA6M50DF00-
B0 SFSRA4M50CF00-
B0 SFSRA5M50EF00-
B0 SFSRA6M00CF00-
B0 SFSRA6M50CF00-
B0 SFSRA5M50BF00-
B0 SFSRA5M74BF00-
B0 KMFC Series
KMFC545
13.0 14.6
4.5 5.5 6 6.5 4.5 5.5 6 6.5 4.5
4.5 4.5 5.5 6.0 6.5 4.5 5.5 6.0 6.5 5.5 5.742
10.7
+90
----------
6
330
+150
+500
6
330
+60 (110) 600 (470) 6 (3.2) +60 (115) 600 (500) 6 (3.6) +60 (115) 600 (500) 6 (4.0) +70 (115) 650 (530) 6 (3.6) +70 (130) 750 (520) 6 (3.0) +80 (150) 750 (640) 6 (3.0) +80 (155) 750 (640) 6 (3.8) +80 (150) 800 (640) 6 (3.4) +125 (180) 800 (740) 6 (3.0)
1000 600 470 470 1000 600 470 470 1000
+125 +70 +80 +80 +80 +60 +60 +60 +80 +50 +50
+ 325
850 6.0 max. 1000 750 6.0 max. 1000 750 6.0 max. 600 750 6.0 max. 470 800 6.0 max. 470 600 6.0 max. 1000 600 6.0 max. 600 600 6.0 max. 470 650 6.0 max. 470 400 8.0 max. 600 400 8.0 max. 600
1400
5
470
Table 10. MHz Filters
1
----------
1
----------
----------------------------------------------------------------------------------
30 (0 4.5MHz) 30 (0 5.5MHz) 30 (0 6.0MHz) 30 (0 6.5MHz) 30 (0 4.5MHz) 30 (0 5.5MHz) 30 (0 6.0MHz) 30 (0 6.5MHz) 25 (0 4.5MHz)
----------------------------------------------------------------------------------------------------
25 (0 4.5MHz) 30 (0 4.5MHz) 30 (0 5.5MHz) 30 (0 6.0MHz) 30 (0 6.5MHz) 30 (0 4.5MHz) 30 (0 5.5MHz) 30 (0 6.0MHz) 30 (0 6.5MHz) 30 (0 5.5MHz) 30 (0 5.742MHz)
2.0 23 (8 - 13MHz)
1.5 0.8
----------------------------------------------------------------------------------
----------------------------------------------------------------------------------------------------------------------
Page 52
PZT Application Manual
PZT Application Manual
Figure 45: MHz Filter Selection Chart
Page 53
Applications
One of the primary uses of band pass filters is in receivers. The simplest receiver is called a super heterodyne receiver (Figure 46). This receiver uses two band pass filters to select the desired signal. The first filter is a wide bandwidth filter that helps reduce noise and extraneous signals. The local oscillator then mixes down the signals and the second band pass filter selects the correct IF frequency. In the USA, the IF for AM radio is 455kHz and the IF for FM radio is 10.7MHz. The signal then goes to an amplifier and then to a discriminator that strips away the carrier signal.
Antenna
RF Amp
Mixer
IF Amp Detector
BP Filter 1
BP Filter 2
~
Local Oscillator
Figure 46: Super Heterodyne Receiver
The second type of receiver is the double super heterodyne receiver (Figure 47). This receiver uses three band pass filters and two local oscillators. The first filter helps reduce noise just as before. The first local oscillator mixes the signal down to the first IF. The second filter selects only this IF frequency to pass on to the rest of the circuit. The second oscillator mixes the signal down to the second IF which is 455kHZ or 10.7MHz as before. The third filter selects only these second IF frequencies to pass to the detector. This receiver has better selectivity due to the increased filtering and the smaller jump when the frequencies are mixed down.
Antenna
RF Amp
Mixer 1
Mixer 2
IF Amp Detector
BP Filter 1
BP Filter 2
BP Filter 3
~
1st Local Oscillator
~
2nd Local Oscillator
Figure 47: Double Super Heterodyne Receiver
TV Filter Application
Murata's SFSH series was originally designed for TV applications but has found wide use in the communications industry. These filters are designed to filter out the sound IF of a TV signal. A television signal has three parts: a sound sig-
Page 54
PZT Application Manual
nal, a picture signal, and a color or chroma signal (Figure 48).
1.25MHz
6MHz 4.5MHz
3.58MHz
1
2
1) Picture Signal (fp) 2) Chroma Signal (fc) 3) Sound Signal (fs)
3
Figure 48: TV Channel Spectrum Description (NTSC-M)
A basic television receiver is shown in Figure 49.
Tuner SAW VIF Amp VIF Det.
Trap
Picture Signal
Filter
Amp
FM Det.
Sound Signal
Figure 49: Inter-Carrier System
First a tuner shifts the desired channel to IF frequencies. A SAW filter selects only the IF frequencies and rejects all others. An amplifier increases signal strength and a detector demodulates the video signal. The signal is then split into two and a trap, or band reject filter, removes the sound IF before the signal is sent to the video signal processing circuit that drives the picture tube. On the other side, a filter, like Murata's SFSH series, removes the picture and chroma signals. A detector then demodulates the sound signal and it is sent to the speaker on the TV set. The trap is a band reject filter meaning that it will allow all frequencies to pass through it except a certain band. In this application, the trap allows all frequencies except the sound IF to pass. Murata also produces SAW filters and discriminators for sound signal detectors.
PZT Application Manual
Page 55
Piezoelectric Traps
Introduction
Piezoelectric ceramic traps are band reject filters originally designed to remove the sound signal in a television receiver. The ceramic traps operate at the same frequencies as the MHz sound IF filters (3.58MHz to 7.0MHz) However, they have found wide use in other areas of the communications industry. A band reject filter is a filter that allows all but a certain range of frequencies to pass unaffected. Figure 50 shows an example of an ideal band reject filter.
Amplitude
Amplitude
Input to the filter
Output of the filter
Original Level Ideal Band Reject Filter
IDEAL
Frequency
Frequency
Figure 50: Ideal Band Reject Filter
Practically, such performance is not physically possible. There will be some attenuation of all frequencies and the sides of the band will not be perfectly straight. This is due to parasitic losses associated with the physical properties of the filter. Figure 51 shows a practical band reject filter.
Amplitude
Amplitude
Input to the filter
Output of the filter Original level
Practical Band Pass Filter
Practical
Frequency
Frequency
Figure 51: Practical Band Reject Filter As can be seen from the figures, the outputs are quite different. The next section will go into how the trap works.
How Does It Work
A ceramic trap is essentially a ceramic resonator. It has the impedance response shown in Figure 52.
Page 56
PZT Application Manual
Impedance |Z| ()
fr
fa
Frequency
Figure 52: Resonator Impedance Response
A ceramic resonator has an impedance minimum at the resonant frequency, fr, and an impedance maximum at the anti-resonant frequency, fa. The resonator is designed so that the resonant frequency is at the frequency that is to be removed. The resonator is then placed to ground in the circuit (Figure 53).
Rline
RS
~ VS
Trap
RL
Figure 53: Single Element Trap Circuit
Frequencies at and near the resonant frequency see a low impedance to ground and are pulled down. All other frequencies see a large impedance and go past the trap to the rest of the circuit. The resulting filter trap response is shown in Figure 54.
PZT Application Manual
Page 57
Amplitude
Frequency
Figure 54: Trap Response
There are two types of trap: single element and double element.
· Single Element Trap Single element traps have two terminals attached to electrodes on either side of a ceramic substrate (Figure
55).
Substrate
t
Electrode
Figure 55: Single Element Trap These traps are low cost, non-tunable devices that offer good attenuation over a set bandwidth.
Page 58
PZT Application Manual
· Double Element Trap With a double element trap, one electrode is cut into two. This allows multi-coupling mode operation and provides better attenuation (Figure 56).
Symmetrical Mode
IN
OUT
GND
Anti-Symmetrical Mode
Figure 56: Double Element Trap
These traps provide better attenuation than the single element traps and are still non-tunable. One other difference is that the bandwidth of these traps can be changed by placing an inductor between the two terminals of the cut electrode (Figure 57). By changing the inductance of the inductor, the bandwidth can be altered to meet the needs of a specific application.
RLine
LS
RS
~ VS
Trap RL
Figure 57: Double Element Trap Circuit
This circuit was simulated on a computer using four different values for the inductor. Figure 58 shows the resulting trap responses for the different values. Figure 59 shows the same responses over a narrower frequency range.
PZT Application Manual
Page 59
Attenuation
20.0
10.0
0.0
-10.0
-20.0
-30.0
-40.0
20u LS 15u LS
-50.0
10u LS 5u LS
-60.0
0.0 1.0 2.0 3.0 4.0 5.0 6.0 7.0 8.0
Frequency
Figure 58: Computer Simulation of a Double Element Trap
Page 60
Attenuation (dB)
20 10
0 -10 -20 -30 -40 -50 -60
4.0
4.2
4.4
4.6
Frequency (MHz)
20u LS 15u LS 10u LS 5u LS
4.8
5.0
Figure 59: Computer Simulation of a Double Element Trap
PZT Application Manual
Murata also makes traps with two and three responses for systems that have multiple IFs. As an example, the PAL TV system used primarily in Europe has multiple sound Ifs depending on the language used. Multiple trap responses are needed to remove the signals that are in the undesired language.
Applications
Ceramic traps were originally designed to be used in TV receivers to remove the sound signal. Figure 60 illustrates a television signal.
1.25MHz
6MHz 4.5MHz
3.58MHz
1
2
1) Picture Signal (fp) 2) Chroma Signal (fc) 3) Sound Signal (fs)
3
Figure 60: TV Channel Spectrum Description (NTSC-M)
The sound signal is centered at the high end of the channel while the picture and color or chroma signals are centered at the low end of the channel. Figure 61 shows a block diagram of a television receiver.
Tuner SAW VIF Amp VIF Det.
Picture Trap Signal
Filter
Amp
FM Det.
Sound Signal
Figure 61: Inter-Carrier System
In the receiver, the tuner down-converts the desired channel to the IF frequencies. The SAW filter then selects the IF frequencies and the amplifier increases the signal strength. A VIF detector strips away the carrier wave from the picture signal. From here the signal is split into two. The first signal passes through a filter, which filters out the picture and chroma signals and passes the sound signal. It then goes to a detector, which strips away the carrier wave and then to the speaker on the television set. The second signal goes through the trap, which removes the sound signal and then to the video processing circuits that drive the picture tube. It is necessary to remove the sound signal because it could cause interference in the picture signal.
Parts
Figure 62 shows an example of the Murata part numbering system for ceramic traps.
PZT Application Manual
Page 61
TPS 3.58 MJ
Series Frequency Type See list of available
series
Figure 62: Trap Part Numbering system Table 11 lists the different series of traps offered by Murata. Some older parts are listed for reference purposes, therefore if a part series has an asterisk (*) by it, then it is obsolete or no longer available for new designs.
Trap Series TPS...MJ TPS...MB* TPSRA-M-B
MKT
Description 2 terminals, for sound IF in B/W receivers or chroma signal in video
3 terminals, 2 elements, for sound IF of TV/CATV receivers 3 terminals, 2 elements, for sound IF of TV/CATV receivers
High frequency trap
Table 11. Trap Series Description
Page 62
PZT Application Manual
Piezoelectric Discriminators
Introduction
Ceramic discriminators are designed to be used in quadrature detection circuits to remove a FM carrier wave. These circuits receive a FM signal, like in a FM radio, and send out an audio voltage, the music that comes out of the speakers. Ceramic discriminators replaced tuned LC tank circuits with a single, non-tunable, solid state device. In order to explain how a discriminator works, it is necessary to briefly explain frequency modulation.
Principles of Frequency Modulation
Frequency modulation (FM) is a method of placing a signal onto a high frequency carrier wave for transmission. The signal is usually an audio signal, such as voice or music, at a low frequency referred to as the audio frequency (AF). This is also referred to as the modulating signal since it is used to modulate the carrier wave. The carrier wave is a high frequency signal that is used to carry the audio signal to a remote receiver. This is referred to as the radio frequency (RF) signal. For FM, the frequency of the RF signal is varied instantaneously around the center frequency in proportion to the AF signal. As the voltage level of the AF signal increases, the frequency of the RF signal is increased. As the AF voltage decreases, the frequency of the RF signal is decreased. Figure 63 illustrates this.
AF Signal
RF Signal
RF Signal Modulated By The AF Signal
Figure 63: Generating An FM Signal
The difference between the highest frequency (when the AF is at a maximum) and the lowest frequency (when the AF is at a minium) is called the frequency deviation. It is the function of the discriminator to recover the audio signal from this modulated RF signal by a method called quadrature detection.
Principles of Quadrature Detection
Quadrature detection is one method of stripping away a FM carrier signal and leaving the original transmitted signal.
PZT Application Manual
Page 63
The block diagram of a quadrature detector circuit is shown in Figure 64.
Limiting Amplifier IF In
Phase Shifter
Mixer
Amplifier
LPF
Recovered Output
Discriminator Rp Circuit
LS
Figure 64: Block Diagram of a Quadrature Detection Circuit
First, the IF signal is passed through a limiting amplifier where any AM signal is removed. From here, the signal is split into two parts. The first part is sent to a phase shifter. This phase shifter is a capacitor, which adds a 90o phase shift to the signal. A discriminator circuit, consisting of a discriminator and a parallel resistor (a series inductor may or may not be included and will be discussed later in the text), then adds an additional phase shift to the signal. The amount of phase that is added depends on the instantaneous frequency of the RF signal. The signal is then sent to a mixer. The second part of the signal is sent straight to the mixer. A low pass filter then removes any high frequency noise and gives an average value for the mixer output. An amplifier then increases the signal strength. The limiter provides an output signal that has a constant amplitude, eliminating any noise or amplitude modulation that may be on the incomming signal. This stage also provides a balanced output, which is important for common-mode noise rejection. This section also provides automatic gain control because its output signal is between a minimum value and a maximum value, constant in amplitude.Figure 65 shows an example of a limiter circuit.
From IF Amp
To FM Demodulator +
-
Figure 65: Limiter Circuit From the limiter, the signal goes on to a balanced demodulator circuit, which includes the discriminator and the mixer
Page 64
PZT Application Manual
(Figure 66)
From Limiter
VCC
IL RS
Q Q 1A 1B
Q Q 2A 2B
Vout To LPF
X
V2
RP
Q1
Q2
LS
V1
Figure 66: Balanced Demodulator Circuit In Looking at the mixer portion of the demodulator circuit, it can be seen that current IL will flow only when V1 and V2 are opposite voltages. This will cause a voltage drop across resistor RS so will give a lower output voltage. Figure 67 shows how the output differs with the input. A square wave is shown to simplify the drawing, but the same principle applies for a sine wave. A low pass filter will average the output pulses into a DC voltage, also shown in the figure below.
+ V1 0
+ V2 0 -
IL
VDC
Figure 67: Signals in the Mixer Circuit The discriminator will add more phase to the lower frequencies and less phase to the higher frequencies. This means that the demodulator will output a large voltage for input signals with a high frequency and a small voltage for signals
PZT Application Manual
Page 65
with a low frequency, thereby recovering the original audio signal (Figure 68)
V1
V2
Vout
LPF Out Figure 68: Input And Output Signals
The discriminator circuit was originally a LC tank circuit (Figure 69a). This circuit had to be hand tuned to the correct IF frequency. Ceramic discriminators replaced the tank circuit with a solid state device that does not require tuning (Figure 69b). The next section will discuss the operation of the discriminator.
IN
OUT
IN
OUT
Rp LS
(a)
(b)
Figure 69: Discriminator Circuit
Principles of Bridge-Balance Detection
Another method of detection is to use a balanced bridge circuit. This circuit consists of 3 resistors and the discriminator connected in a bridge configuration. The output goes into a subtractor and then to the balanced demodulator circuit
Page 66
PZT Application Manual
shown earlier (Figure 70).
IF In
Limiting Amplifier
Balanced Demodulator LPF
Amplifier
Recovered Output
Discriminator
Vin
A
R1 1k
R2 1k
B R3
1k
VB VA Subtractor
Vout
Figure 70: Balanced Bridge Circuit
This circuit utilizes both the impedance and phase responses of the discriminator. The discriminator is designed to be about 1k at the center frequency, so the other resistors are all 1k. This means that as the frequency changes, the impedance and phase of the discriminator will change. This change will result in a phase shift being added to the original signal. The subtractor will take the voltage difference between points A and B and reference it to ground so that it can be fed into the balanced demodulator. Although the operation is different, the output signal of the subtractor is the same as the output signal of the quadrature detection circuit.
How Does It Work
Piezoelectric ceramic discriminators are similar to ceramic resonators. They have the impedance and phase response shown in Figure 71.
fa
fr
Impedance|Z| ()
+90
Phase (deg)
0
CL
C
-90
Frequency
Figure 71: Resonator Impedance and Phase Plot
PZT Application Manual
Page 67
As can be seen from Figure 71, the impedance is a minimum at the resonant frequency, fr, and a maximum at the antiresonant frequency, fa. Between these two frequencies the discriminator becomes inductive and is capacitive over all other frequencies. As stated earlier for the quadrature detection circuit, it is desired to add more phase to the lower frequencies and less phase to the higher frequencies. By adding a resistor in parallel with the discriminator, the anti-resonant impedance is lowered and the phase response is dampened. Figure 72 shows a computer simulation of the phase response of the resonator using different values for a parallel resistor.
10 0 .0 80.0 60.0 40.0 20.0
0.0 - 20.0 - 40.0 - 60.0 - 80.0 - 10 0 .0
No RP 25k RP 10k RP 1k RP
Frequency (M Hz)
Figure 72: Computer Simulation of Resonator With Parallel Resistor
A series inductor increases the bandwidth, but this shifts the anti-resonant frequency to a higher frequency. Figure 73 shows a computer simulation of the phase response using different values for the series inductor. It also improves the symmetry of the output response. Since the inductor can also shift the center frequency of the discriminator, the design of the discriminator must compensate for this. The inductor is used for applications requiring a wide bandwidth and is generally not necessary for all applications. This manual shows the inductor in all of the circuits as a reference,
Page 68
PZT Application Manual
but the specific application and an IC characterization (Appendix 3) determine if it is really necessary.
10 0 .0 80.0 60.0 40.0 20.0
0.0 - 20.0 - 40.0 - 60.0 - 80.0 - 10 0 .0
No LS 10u LS 20u LS
Frequency (M Hz)
Figure 73: Computer Simulation of Resonator With Parallel Resistor and Series Inductor
From Figure 73, it can be seen that the lower frequencies would have the largest phase shift added and, as a result, would have the lowest output voltage. When a comparison is made between output voltage and frequency the result is
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that the circuit has an S curve charateristic (Figure 74).
out V (Audio Out)
Frequency
Figure 74: Discriminator S Curve Characteristic
When the discriminator is well tuned, the center of the S curve is at the IF frequency. This results in the best overall recovered audio or output voltage and also provides a margin against variations in the center frequency from part to part (Figure 75).
out V (Audio Out)
FHP FLP
Output Signal
Frequency
FM Signal
Figure 75: Well Tuned Discriminator If the discriminator is poorly tuned and the center of the S curve is not near the center frequency, then the recovered
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audio and the bandwidth would be decreased (Figure 76).
out V (Audio Out)
FHP
FLP Frequency
Output Signal
FM Signal
Figure 76: Poorly Tuned Discriminator
If the signal were at the minimum, FLP, or maximum, FHP, of the S curve, then the recovered audio would be a minimum and the signal would be distorted. As can be seen in Figure 77, the lower half of the wave is flipped up and a series of humps results. This leads to a completely unrecognizable output signal.
out V (Audio Out)
FHP
FLP Frequency
Output Signal
FM Signal
Figure 77: Distorted Output Signal Peak separation is the distance between FLP and FHP. A wider peak separation gives more linear characteristics at the
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center of the S curve and a wider bandwidth, but it also gives a lower recovered audio voltage (Figure 78).
Wide Peak Separation
out V (Audio Out)
FHP
FLP Frequency
Output Signal
FM Signal
Figure 78: Wide Peak Separation A smaller peak separation has a smaller bandwidth but gives a larger recovered audio voltage (Figure 79).
Small Peak Separation
out V (Audio Out)
FHP
FLP Frequency
Output Signal
FM Signal
Figure 79: Narrow Peak Separation
Figure 80 shows an example of recovered audio data. Frequencies near the center frequency result in the largest output voltage. The 3dB frequencies are the two points where a line 3dB down from the maximum recovered output intersects the curve. The 3dB bandwidth is the range of frequencies between these two points, and should be close to the
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Audio Output
frequency deviation. The two minimum points on the recovered audio curve correspond to FHP and FLP of the S curve.
3dB Bandwidth 3dB
Frequency
Figure 80: Recovered Audio Curve Some distortion is introduced by the discriminator because it is not a truely linear divice., as shown by the "S" curve in Figure 81.
out V (Audio Out)
AF Level
Distortion
Fdev
Frequency
Figure 81: Discriminator Distortion This distortion is smallest at the center frequency of the discriminator where the discriminator is at its most linear point. This distortion can be compensated for in the design of the circuit and minimized by a good discriminator. Figure 82 shows an example of a graph of recovered audio and total harmonic distortion for the quadrature detection circuit. The bridge detection circuit has a more linear phase characteristic, resulting in a wider bandwidth and flat distortion (Figure
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83). 1000
100
Output Voltage [mV]
100 10
AF Output Voltage [mVrms] T.H.D [%]
10
1
T.H.D. [%]
1
0.1
0.1
0.01
440
445
450
455
460
465
470
Frequency [kHz]
Figure 82: Example of Recovered Audio and Total Harmonic Distortion for Quadrature Detection
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1000 100
Output Voltage [mV]
100 10
AF Output Voltage [mVrms] T.H.D [%]
10
1
T.H.D. [%]
1
0.1
0.1 10.3
10.4
10.5
10.6
10.7
10.8
10.9
11.0
0.01 11.1
Frequency [MHz]
Figure 83: Example of Recovered Audio and Total Harmonic Distortion for Bridge Detection
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Applications
IC Characterization Service
The ceramic discriminators produced by Murata may or may not work with all chips using standard external circuit values. This is mainly due to typical variations in IC manufacturer detection circuits, part family to part family or IC maker to IC maker. In order to assist our customers with their designs, Murata offers a chip characterization service free of charge. The chip that our customer is using is tested with the Murata discriminator and the discriminator frequency will be adjusted for the particular IC. Murata provides the engineer the recommended Murata part number that should be used with their target IC and the recommended external hook up circuit for this target IC. This enables the designers to adjust their designs so that the discriminator will work every time. These adjustments can be as simple as adjusting component values or as complicated as redesigning the entire circuit. Murata Electronics sales representatives are able to arrange IC characterizations. Please try to start the IC characterization process with Murata as soon as possible, since it does take time to do an IC characterazation and there can be several customers at any one time waiting for this service. Please see Appendix 3 for more information on this service and the needed forms. Piezoelectric ceramic discriminators are used in the detector stage of receivers. In Figure 84, the detector block is the circuit shown in Figure 64. The output of this circuit would then go to a speaker.
Antenna
RF Amp
Mixer 1
Mixer 2
IF Amp Detector
BP Filter 1
BP Filter 2
BP Filter 3
~
1st Local Oscillator
~
2nd Local Oscillator
Figure 84: Double Super Heterodyne Receiver
Parts
Figure 85 gives an example of the Murata part numbering system for discriminators.
CDA 10.7 MG A 15
Series
See list of available
series
Frequency Type (Mhz)
Type A = FM IF detector G = FM IF detector C = 3 terminal quadrature detector E = 2 terminal quadrature detector
IC indicator
Figure 85: Discriminator Part Numbering System
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Table 12 lists the different series of discriminators offered by Murata and gives a brief description of each series. Some older series are shown for reference purposes, so all series with an asterisk (*) are not available for new designs and may be obsolete
Discriminator Series CDA...MG CDA...MC CDA...MA
CDA (4.5-6.5) ME(MD)* CDA (4.5-6.5) MC* CDSH(4.5-6.5) ME CDSH(4.5-6.5)MD CDSH(4.5-6.5) MC CDB...C CDBM...C CDB...CL CDBM...CL CDBC...CX CDBC...CLX CDBCA* CDACV CDSCA
Description Wide bandwidth, low recovered audio, 2 terminals Narrow Bandwidth, high recovered audio, 2 terminals
3 terminal device Quadrature detection, 2 terminals Differential Peak detection, 3 terminals Quadrature detection, 2 terminals Differential Peak detection, 2 terminals Quadrature detection, 3 terminals kHz discriminator, no series inductor
Miniature version of CDB...C Wide bandwidth, used with series inductor
Miniature version of CDB...CL Not used with series inductor, narrow bandwidth, 2 terminals
Used with series inductor, wide bandwidth, 2 terminals Surface mount device, 2 terminals + 1 dummy terminal
MHz surface mount discriminator MHz surface mount discriminator
Table 12. Discriminator Series Description
SMD/Leads Leads Leads Leads Leads Leads Leads Leads Leads Leads Leads Leads Leads SMD SMD SMD SMD SMD
Appendix 5 shows a list of ICs that have been characterized by Murata and the recommended discriminator for each IC.
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Page 78
Surface Mount
h Series ductor
Without Series Inductor
START kHz Discriminators
With Dummy Terminal
Standard
CDBC...CLX
CDBC...X
CDBCA (Limited Availability)
Leaded
Miniature
With Series Inductor
Without Series Inductor
CDBM...CL
CDBM...C
Figure 86: kHz Discriminator Selection Chart
With Series Inductor
Without Series Inductor
CDB...CL
CDB...C
PZT Application Manual
PZT Application Manual
Narrow Bandwidth
Surface Mount
CDACV...MC
Wide Bandwidth
CDACV...MG
START MHz Discriminators
Quadrature Detection
Leaded
Differential Peak Detection
CDSH(4.5-6.5)MD
Figure 87: MHz Discriminator Selection Chart
TV CDSH...ME
FM
Wide Bandwidth
Narrow Bandwidth
CDA...MG
CDA...MC
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Surface Acoustic Wave Filters
Introduction
Surface acoustic wave (SAW) filters provide excellent filtering properties at high frequencies. This makes them suitable for use in many wireless communications products such as cellular telephones, cordless telephones, TVs, VCRs, cable modems, and pagers.
How Does It Work
SAW filters use Inter Digital Transducers (IDT) as the input and output electrodes mounted on a piezoelectric substrate. An IDT is a comb structure consisting of interleaved metal electrodes, called fingers, attached to a bus bar (Figure 88).
Bus Bar o
Finger
Absorber Input
IDT
Lead Wire
Piezoelectric Substrate
Output
Input IDT
Output IDT
Figure 88: SAW Filter Construction
By applying a signal at the input terminal, stress is created between the electrodes by the piezoelectric effect. This stress causes the substrate to shrink and expand, forming a surface acoustic wave which propagates along the substrate to the output IDT. At the output IDT, the wave causes a potential difference between the electrodes, which is then seen as a voltage at the output terminals. The maximum amount of energy transfer occurs when the wavelength of the surface acoustic wave is the same as the distance between electrodes, . All other wavelengths are attenuated. Because of this, adjusting the pitch of the electrodes sets the center frequency of each overlapping finger section. This procedure is called variable pitch. Adjusting the finger overlap length can change the magnitude of the signal transmitted or received by each overlapping finger section. This procedure is called apodization. This is a transversal filter that enables the amplitude and GDT characteristics to be designed separately. This allows a flat passband, good
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selectivity, and a flat GDT to be acheived (Figure 89). A wide range of frequency characteristics can be realized just by the design of the IDT electrode pattern. Since the signal is propagated in both directions from the IDT, silicon absorbers are placed at the edges of the substrate to prevent reflections from the edge that would cause distortion.
Amplitude Characteristic
GDT Characteristic
Figure 89: SAW Filter Characteristics
Causes of Signal Distortion
There are two main causes of distortion in SAW filters. The first is called direct breakthrough. This is when the signal is powerful enough to be picked up at the output without having traveled through the piezoelectric material. The signal is seen at the output attenuated but unfiltered before the filtered signal is seen. The other type of distortion is called triple transit echo (TTE). This is a result of the signal bouncing between the two IDTs. If the signal takes time to be seen at the output then the TTE signal will be seen 2 after the main signal. Figure 90 illustrates the signal paths and Figure 91 shows the input and output as a function of time.
1 2
~
3
1) Direct Breakthrough 2) Main Signal 3) T.T.E. Figure 90: SAW Filter Signal Paths
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Input
Direct Breakthrough
Main Edge Reflection, Signal Bulk Wave
Time T.T.E.
2
Time
Figure 91: SAW Filter Signal Timing
TTE tends to cause a ripple in both the amplitude characteristic and in the GDT, which can cause errors in digital systems, and in the amplitude characteristic, which results in signal distortion. In TVs, because of the delay, this can cause a ghost image to the right of the main image. Direct breakthrough also causes ripples in the GDT and amplitude characteristics as well as deterioration in attenuation level outside the pass band. Signals that should not pass could then cause interference later in the circuit. In TVs, this can cause a ghost image to the left of the main signal. In order to minimize the signal attenuation in the filter it is desirable to minimize the insertion loss in the filter. The insertion loss is not the same as the power loss. We distinguish between power loss and insertion loss in the following way: insertion loss is the ratio of output voltage when the filter is shorted to the maximum output voltage when the filter is inserted; power loss is the ratio of the available power of the source to the power supplied to the load. Numerically,
Voltage
loss
=
20
log
VS VL
Insertion
Loss
=
Voltage
Loss
-
20 log
RS
+ RL RL
Power
Loss
= Voltage
Loss
+ 10 log
RL 4RS
Where: VS = source voltage VL = load voltage RS = source resistance RL = load resistance
Common practice to reduce insertion loss is to conjugately match the input and output impedances. SAW filters have a capacitive component in input and output impedance, which can be cancelled by adding inductors. The purely resistive components of the filter impedance can be matched with RS and RL. However, the TTE level and power loss are inversely related: when the power loss is reduced the TTE increases. As a result, it is necessary to greatly mismatch the filter. For practical uses a 40dB suppression of TTE is required which requires a theoretical power loss larger than 16dB. Adding a safety margin, the actual power loss should be greater than 18dB. The level of direct breakthrough has three main causes. The first is electrostatic causes like stray capacitances. The second is electromagnetic inductions due to the currents passing through the printed pattern. To limit these effects, the printed input and output patterns should be made small and short and the VIF stage should be shielded from the other stages. The last cause is ground loops. There are a number of places on the board where the earth grounds are mutually connected. These should be cut where possible to limit the number of loops.
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Applications
Television, Cable, and VCR
The most common use of SAW filters is in television receivers. A television signal has three parts: a sound signal, a picture signal, and a color or chroma signal. These three signals are placed in a 6MHz frequency band called a channel. Within the 6MHz band, the video carrier is centered at 1.25MHz from the low end and the sound carrier is centered at 250kHz from the upper end. This leaves a 1.5MHz guard between the adjacent channels to prevent interference. The chroma carrier is centered at 3.58MHz from the video carrier. Figure 92 illustrates the television signal.
1.25MHz
6MHz 4.5MHz
3.58MHz
1
2
1) Picture Signal (fp) 2) Chroma Signal (fc) 3) Sound Signal (fs)
3
Figure 92: TV Channel Spectrum Description (NTSC-M)
Television receivers all have the same basic parts. The first part is an antenna or, in the case of cable television, a cable. The antenna receives all channels simultaneously, spread across the frequency spectrum. The next part is a tuner that selects the desired channel by using a local oscillator to bring the channel frequencies down to the IF frequencies. The IF frequencies are the frequencies that the rest of the receiver is tuned to and uses to produce the picture and sound. The oscillator frequency is adjusted by the user and forms a reference signal. All of the signals from the antenna are subtracted from the reference signal and the desired channel is reduced to the IF frequencies and reversed. For example, channel 6 lies in the range from 82 to 88 MHz. As stated before, the video carrier is 1.25MHz above the low end, which is 83.25MHz, and the sound carrier is 4.5MHz above this, or 87.75MHz (Figure 93a). The standard IF frequencies in the U.S.A. are 45.75MHz for the picture and 41.25MHz for the sound. By tuning the oscillator to 129.00MHz, the channel 6 video carrier becomes 129 83.25 = 45.75 and the sound carrier becomes 129 87.75 = 41.25. This reduces the signal to the IF frequencies and inverts the signal, the video signal is now higher than the sound signal (Figure 93b). All of the frequencies in the antenna are treated in this manner and then sent to the next stage.
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fp
fc
fs
(a) Channel 6 TV
signal received in
the antenna
82 83.25 fs
MHz fc
87.7588
fp
(b) Channel 6
TV signal after
leaving the
tuner
4141.25
MHz
45.75 47
Figure 93: TV Channel Conversion
The third stage is a SAW filter. This filter selects the signals only in the IF frequencies. All others are rejected. To continue the example above, the tuner has reduced the channel 6 signals to the IF frequencies. Since the SAW filters only pass the IF frequencies, only the channel 6 signals are sent on to the rest of the receiver. This stage begins what is called the tuned part of the receiver. The rest of the receiver is adjusted so that only the signals in the IF frequencies are seen or manipulated and the operator does not have to adjust anything else. The next part is an amplifier that increases the signal strength. The amount of energy received at the antenna is very small and even more is lost in the previous stages. This stage boosts the strength to a point that the following stages can more effectively use. The next stage is an IF detector that strips away the carrier signals reducing the signals to the baseband (0 6MHz) and inverting them using the same method as the tuner. Next the signal is split two ways. One part is passed through a filter that selects only the sound information. This information is passed to an amplifier and then to a FM detector where the signal is demodulated. From here the signal goes to the speaker on the TV. The other part is passed through a trap that selects only the picture and chroma information. This information is sent to an amplifier and then to the picture tube circuitry. This is the basic idea behind the receiver, though there are a few different kinds with slightly different designs.
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Figure 94 shows a diagram of a basic receiver and the resulting signal after each section.
Tuner SAW VIF Amp VIF Det.
Trap
Picture Signal
Filter
Amp
FM Det.
Sound Signal
Figure 94: TV Signal In A Receiver
Types of TV, VCR, and Cable Receiver There are three main kinds of receiver used in television, cable, and VCRs. The first is the inter-carrier system (Figure 95). This system is the basic system described above. This is the cheapest and simplest system but suffers from "buzz" which results from the picture signal breaking into the sound signal.
Tuner SAW VIF Amp VIF Det.
Trap
Picture Signal
Filter
Amp
FM Det.
Sound Signal
Figure 95: Inter-Carrier System
The second kind of receiver is called the quasi-parallel system (Figure 96). This system has two SAW filters after the tuner: one to select the picture and chroma IFs and one to select the sound and picture IFs. The picture and chroma signals go through the amp, VIF detector, and trap as before. The sound and picture signals go through an amplifier and then to an SIF detector where the picture signal is used as a reference to strip away the sound carrier signal. A filter then removes the picture signal, an amplifier increases the signal strength, and a FM detector demodulates the sig-
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nal. This system has better signal separation than the inter-carrier system.
Tuner SAW VIF Amp VIF Det.
Trap
Picture Signal
SAW
SIF Amp
SIF Det. Filter
Amp
FM Det.
Sound Signal
Figure 96: Quasi-Parallel System
The last receiver is called the split-carrier system (Figure 97). It is similar to the quasi-parallel system except that the SIF detector is replaced by an oscillator that converts the sound signal down to the sound IF frequency. Because of this the picture signal is not needed as a reference so the SAW filter selects only the sound IF. This system has the best signal selection and the most complicated design.
Tuner SAW VIF Amp VIF Det.
Trap
Picture Signal
SAW
SIF Amp
Mixer
Filter
~
Local Oscillator
Amp
Figure 97: Split-Carrier System
FM Det.
Sound Signal
Connection of the SAW Filter to Other Stages
The most common way of compensating for the high insertion loss of the SAW filter is by inserting an amplifier. Where the amplifier is inserted and how the stages are connected becomes important to reducing losses and distortion. When the amplifier is placed before the filter, it is called a preamplifier system. Input impedance matching is accomplished by RC in Figure 98. The parallel inductor cancels the capacitive component of the filter input impedance. Increasing the value of RC will increase the gain of the amplifier but will also increase TTE. The output impedance match is accomplished by R3. Here, a higher value for R3 results in a lower TTE, but as stated before, RC should equal R3 for minimum power loss. The values of RC and R3 must be determined by compromising between gain and TTE suppression. Because the signal is amplified to high levels, intermodulation distortion becomes a concern. A common
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way to prevent this is to insert a negative feedback resistor on the emitter.
V+
Tuner
R1
RC
L1
R2
RE1
RE2
SAW
L2
R3
VIF Chip
Figure 98: Pre-amplifier Matching Circuit
The preamplifier system is suited for high impedance SAW filters. For low impedance filters, the resistor values would have to be small to suppress TTE. If RC is too small, then the collector current is limited by the maximum collector dissipation of the transistor and the gain suffers. In order to use a low impedance filter an impedance conversion circuit is required (Figure 99). The capacitance of the SAW filter corresponds to C2 in the conversion circuit, the coil corresponds to L1, and capacitors added in place of the circles in Figure 98 correspond to C1. The transformation ratio is given by C1 : (C1 + C2) and the impedance ratio is given by C12 : (C1 + C2)2. An arbitrary impedance transformation can be set by picking a convenient value of C1. The impedance at the input of the filter can be increased by stepping down and at the output the impedance can be increased by stepping up. In this way, a low impedance filter can be used with the same peripheral circuit.
C1 L1
C2
Figure 99: Impedance Conversion Circuit
The system that places the amplifier after the filter is called a postamplifier system. Figure 100 shows an example of a postamplifier system. The input impedance will have a value around 50 to 100 while the output of the tuner is nominally 75. Since the input of the SAW is not 75 the output circuit of the tuner can be affected. If the impedance is higher than 75, then the Q of the IF output circuit becomes high and the bandwidth becomes narrower. To prevent this, a Q damping resistor should be placed in parallel with the input terminals of the SAW filter. Because of the low signal level after the filter there could be deterioration of the noise figure. For this reason, it is desirable to use a high gain tuner. In order to prevent deterioration of the Signal to Noise ratio the tuner should be able to handle a high signal level
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before AGC begins to operate.
Tuner
SAW
V+
R1
RC
L1
R2 RE
VIF Chip
Figure 100: Post-amplifier Matching Circuit For Low Impedance
The postamplifier design is best used with low impedance filters because the filter termination is limited to a low impedance. To use high impedance filters with this design a tuning coil must be placed in series with the filter input as shown in Figure 101. This will allow a close match at the input that will reduce loss. The large mismatch at the output will cause a high loss that will suppress TTE. In this way, a high impedance filter can be used with the same peripheral circuit.
Tuner
SAW
V+
R1
RC
L1
R2 RE
VIF Chip
Figure 101: Post-amplifier Matching Circuit For High Impedance
If the gain of the VIF chip can be increased then the amplifier becomes unnecessary. The tuner becomes the signal source for the SAW with a fixed impedance of 75 and the VIF chip becomes the load with an impedance between 1k and 3k. Since the source and load have fixed impedances it is necessary to include matching circuits in either the input or the output. For a high impedance filter, a parallel coil can practically match the output of the filter to the input of the chip, or a series coil matches the input of the filter to the output of the tuner as described previously. In the case of a low impedance, the input of the filter is matched to the output of the tuner by a parallel coil, or the output of the filter is matched to the input of the chip by the transformation circuit described above. Both circuits can attain an insertion loss of approximately 10 - 18dB making the amplifier unnecessary. Figure 102 shows diagrams for both types of filter.
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Tuner
SAW
High Gain
VIF Chip
OR
Tuner
(a) High Impedance
SAW
High Gain VIF Chip
Tuner
SAW
High Gain VIF Chip
OR
Tuner
SAW
High Gain VIF Chip
(b) Low Impedance
Figure 102: No Amplifier Matching Circuits
Murata offers a characterization service, free of charge, which will provide a matching circuit for the SAW filter. The customer must provide samples of the IC they intend to use and Murata will provide the output circuit and frequency correlation data. It is recommended that the customer provide a sample of their PC board so that both impedance matching and breakthrough suppression can be evaluated. This ensures the best possible performance of the filter.
Parts
Figure 103 shows the basic part numbering structure Murata uses for its SAW filters.
SAF 32.9 MCA 70Z - TF21
Series Frequency Type
Package Type
Tape Carrier
60Z = low profile package
SAFC = SMD
70Z = standard package
80Z = shielded by conductive resin
200Z = shielded by metal film
210Z = shielded, larger substrate
Figure 103: SAW Filter Part Numbering System
The 80Z and 200Z packages can be supplied in ammo-pack packaging. A SAW filter data book, listing the filters and the system each filter applies to is available upon request.
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BGS Devices
Introduction
Surface acoustic wave (SAW) devices are used in various consumer products, generally above 30MHz because of device size and cost factors. Murata has recently applied a fundamental technology called BGS that significantly reduces size and cost of certain SAW devices. BGS is a combination of the initials of the three scientists who developed the technology for use on PZT ceramics (Bleustein, Gulyaev, and Shimizu). Use of PZT ceramic was not considered practical for mass production because of a number of material related problems, including a large deviation of PZT material quality and the limited availability of PZT ceramics with both a small temperature coefficient and a large coupling factor. There were also fabrication related problems, but Murata has successfully solved these problems, allowing us to develop several new products. With the BGS technology we are able to make resonators, traps, and filters based on a resonator configuration. BGS filters can replace some SAW filters, but availability of the filters is limited by material.
How Does It Work
The idea behind a SAW resonator is to create a standing wave across the substrate and have a single interdigital transducer (IDT) act as both the receiving and transmitting antenna. Conventional SAW filters and resonators utilize what is called a Rayleigh wave (Figure 104 ). This consists of a wave that displaces in two dimensions (X and Z in Figure 104 ). If you imagine a rectangular table, the first part of the wave would be a variation in the thickness of the table (the SV wave). The second part would be compressing the table in the same direction that the wave is traveling (the L wave). This would be like pushing and pulling on the ends of the table. The problem with this kind of wave is that it does not reflect well at the free edge of the substrate. As can be seen in Figure 104, when the SV wave reflects, a spurious P(L) wave component is generated. Likewise, a spurious SV wave is generated when the P(L) wave is reflected. This leads to signal distortion and loss of energy due to the creation of the spurious waves..
Wave Displacement
Z
SV
X
Wave
Y
Reflection at free surface
SV
SV+P(L) air +
Z P(L) Wave
P(L)
X P+SV air
Y
+
Figure 104: Rayleigh Wave Components
To solve this problem, large reflectors are placed on either end of the substrate to guarantee 100% reflection of the Rayleigh wave and a stable standing wave along the substrate (Figure 105). A very large area of substrate must be
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used to accomodate these reflectors. The larger substrate results in a larger part size and an increased cost.
Raleigh wave resonator with reflectors
Reflector IDT
SV Wave
Polar Axis
Propagation L Wave
Displacement
Figure 105: Rayleigh Wave Resonator
The BGS devices use a third kind of wave called the SH wave and do not have the SV or L waves. The SH waves have a displacement parallel to the surface of the substrate, and perpendicular to the direction of propogation. This wave can be simulated by sliding your hand from side to side as you move from one end of the table to the other (Figure 106).
Wave Displacement Reflection at free surface
Z SH Wave
X
SH
air
Y
SH
Figure 106: SH Wave Component
The SH wave can achieve 100% reflection at the free edge of the substrate, allowing us to remove the reflectors from the BGS and SH wave devices. This means we can achieve a 50% to 75% reduction in size (3.8 x 3.8 x 1.5mm typical size for BGS devices). The smaller substrate also allows us to realize a cost reduction over conventional SAW devices (Figure 107).
SH wave resonator using edge reflection
Propagation
Finger
PZT Application Manual
Polar Axis
SH Wave Displacement
Figure 107: BGS and SH Wave Resonators
Page 91
Currently Murata is developing this technology on three different substrates; piezoelectric ceramic (PbZrTiO4 or PZT), Lithium Tantalate (LiTaO3 or LT), and quartz crystal (X'tal). We refer to the PZT substrate devices as BGS devices and the other two as SH wave devices, though they all work in the same way. We are able to achieve a wide range of frequencies and bandwidths with these materials. The following table gives a breakdown of the characteristics.
Substrate Material
PZT
Center Frequency Range (MHz)
20 - 70
Bandwidth Range (%)
1 - 4
Temperature Variation (ppm/oC)
7
Impedance Variation () 50 (No inductor required)
LT
100 - 200
1 - 2
-30
200 - 600 (Inductor required)
X'tal
110 - 300
0.05 - 0.08
1
1k - 1.5k (Inductor required)
Table 13. Characteristics of the BGS and SH Wave Devices
Parts
Murata currently offers BGS VCO resonators as well as traps for television, cable television, and VCR applications. We are developing resonator based BGS filters for 1st IF in cellular applications (GSM and CDMA2000) and actively looking for new markets and applications for this product.
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Piezoelectric Sound Components
Introduction
Murata Electronics' piezoelectric sound components (piezo alarms) are designed for applications requiring a highly reliable acoustic alarm or audible tone signal. Their reliability extends from the fact that they are solid state construction so they have very few moving parts. These devices can produce either a single or multi-frequency output depending upon operating requirements. The tone is distinct due to the absence of harmonics, and gives an extremely clear, penetrating sound. Their high acoustic output versus low input power requirements make them ideal for a wide variety of applications, especially products powered by battery. They are used as indicators or alarms that call a person's attention to the product. These buzzers and speakers are used in products such as phones, pagers, smoke detectors, and appliances like microwaves.
How Does It Work
Sound is simply a wave of varying air pressure. These pressure waves cause a thin membrane in the ear to vibrate and the brain interprets these vibrations as sound. A decibel (dB) scale is used to describe the sound pressure level (SPL) or loudness of a sound. An increase of 20 dB means that the SPL increased by ten times. Figure 108 shows the dB scale.
Sound Pressure Level (dBA)
200 180 Intolerable
140 Painful
100 Uncomfortable
60 Comfortable
20 Perceptible 0
Rocket Engine at Take-off Jet Aircraft Small Aircraft Taking Off
Air Raid Siren Jackhammer Power Lawn Mower Conversational Speech Private Office Whispering
Figure 108: SPL Level Reference
The sound pressure level specification for a buzzer must have three additional pieces of information included. First is the distance from the sound emitting hole that the measurement was taken. The reason for this is that as the sound wave expands outward, it loses strength. The measurement will be louder 10cm from the buzzer hole than it would be 30cm from the buzzer hole. The second piece of information is the frequency at which the buzzer was driven. The buzzer has a resonant frequency that will produce the loudest sound and any other frequency will produce a lower SPL. The last piece of information is the input drive voltage. A higher input voltage will produce a louder sound up to the point at which the material breaks down. Without all of this information an accurate comparison cannot be made between two different buzzers. The sound source of a piezoelectric sound component is the piezoelectric diaphragm. The piezoelectric diaphragm (bender plate) consists of a piezoelectric ceramic plate, with electrodes on both sides, attached to a metal plate (brass,
PZT Application Manual
Page 93
stainless steel etc) with conductive adhesive. Figure 109 shows the construction diagram of a piezoelectric diaphragm.
Electrode Piezoelectric Ceramics
Electrode
Piezoelectric Ceramics
Piezoelectric Element
Piezoelectric Diaphragm
Metal Plate
Figure 109: Piezoelectric Diaphram
The sound is created from the movement of the metal plate. Applying a D.C. voltage between electrodes of the piezoelectric diaphragm causes mechanical distortion due to the piezoelectric effect. The distortion of the piezoelectric ceramic plate expands in the radial direction causing the metal plate to bend shown in Figure 110(a). Reversing the polarity of the D.C. voltage cause the ceramic plate to shrink, bending the metal plate in the opposite direction, shown in Figure 110(b). When an A.C. voltage is applied across the electrodes, the diaphragm alternates bending in the two directions. The repeated bending motion produces sound waves in the air.
(a) Extended
+ _
(b) Shrunk
_
(c) AC Voltage Applied
~
+
Figure 110: Diaphram Operation
Note: Murata does not recommend using a drive signal with a DC bias because it could depolarize the ceramic and limit maximum SPL performance. Typically, the piezoelectric diaphragm alone does not produce a high SPL. It is necessary to mount the diaphragm in a resonant cavity designed to enhance the SPL for a specific frequency.
Design Of The Resonating Cavity
The piezoelectric element alone can not produce a high sound pressure level (SPL). This is because the acoustical impedance of the element does not match that of any open air loading. Therefore a resonating cavity must be built to match the acoustical impedance of the element and the encased air. There are three methods in mounting the piezo diaphragm to a resonating cavity. The method of mounting the diaphragm will effect the sound output. The three methods of mounting are as follows:
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PZT Application Manual
· Node Support
The diaphragm is mounted at a node, a circumference where no vibration takes place. This method causes the least mechanical suppression of vibration and thus provides the highest SPL and the most stable oscillation frequency of the three methods. Node support enhances only a narrow range of frequencies but does so very well. The frequency of the sound output will equal the piezo diaphragm resonant frequency.
· Edge Support
The diaphragm is mounted at the outer edge of the disk causing the entire disk to vibrate. This method suppresses the fundamental frequency by moving the node but provides a possibility of a wide frequency response. The frequency output will be approximately half of the piezo diaphragms resonant frequency.
· Center Support
The diaphragm is mounted at the center of the disk causing the outer edge to vibrate. This method provides the lowest SPL since the main vibration area is forcefully supported. This method is not useful due to design difficulties.
Figure 111 illustrates the different support methods.
fo
(a) Node Support
fo/2
(b) Edge Support
fo/2
(c) Central Support
Figure 111: Mounting Methods The resonant frequency of the cavity is obtained from Helmholtz's Formula.
fo = c 2
4a2 d 2h(t + ka)
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fo = Resonant frequency of cavity (Hz) c = sound velocity 34.4x103 cm/sec @ 24oC a = radius of sound emitting hole (cm) d = diameter of support t = thickness of cavity k = constant 1.3
The buzzer diagrams in Figure 112 show what is being specified by the equation variable "a", "d", "t", and "h".
d
2a t h
d
2a t h
(a) Node Mount
(b) Edge Mount
Figure 112: Cavity Measurements For Helmholtz's Formula
By designing the diaphragm and the cavity to have the same resonant frequency, the SPL is maximized and specific bandwidths can be provided.
Drive Procedure
There are two ways to drive piezoelectric sound components: External-Drive and Self-Drive
· External Drive
This drive method is typically used with edge mounted devices and uses an external oscillating circuit to produce sound. In this way the device can act as a speaker and produce frequencies over a specific bandwidth. This type of drive method is used when multiple tones are desired. Externally driven devices have found extensive use in watches, calculators, game machines, as well as appliances like microwave ovens, washing machines, and TVs.
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PZT Application Manual
· Self Drive
This method is used with node mounted devices. The diaphragm has a feedback tab on one of the electrodes that is used in closed loop Hartley types of oscillation circuits. When the circuit is closed to the resonant frequency, the conditions for oscillation are met and the diaphragm produces a single high-pressure tone. This type of drive procedure will produce only one tone but will have the highest SPL possible from the buzzer.
Figure 113 illustrates the two drive types.
(a) Self-drive Oscillation Type
Self-drive Circuit
(b) External-drive Oscillation Type
External-drive Circuit
Resonating Supported Part Sound Lead Oscillator Power
Case (Cavity) (adhesives) Element Wire
Source
Figure 113: Two Drive Oscillation Types Figure 114 gives a simple example of an external drive circuit.
INV. 1 INV. 2 INV. 3
R2
R1
C
OUT
Figure 114: Example of External Drive Circuit
INV.1 and INV. 2 Make an astable oscillator while INV. 3 acts as a buffer and a waveform shaper, providing a sharp square wave output. The equation for the circuit is:
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fosc =
1
2.2 R1C
R2 10R1
Resistor values can range from about 3k to about 10M. Capacitor values can range from 50pF up, though below 1000pF the frequency will be somewhat lower than predicted by the equation. The input resistor, R2, is normally made 10 times the timing resistor, R1, to minimize the output curving effect of the protection diodes in the inverter. By adding a fourth inverter between the leads of the external drive buzzer, a push-pull circuit is made (Figure 115). If one terminal of the buzzer were connected to ground and the other to the output of the inverter, the buzzer would see a voltage only on one terminal. The element would only deflect in one direction. By adding the fourth inverter, a voltage can be applied to both pins and the element will deflect in both directions. This doubles the voltage across the buzzer and increases the SPL.
INV. 1 INV. 2 INV. 3 INV. 4
R2
R1
C
Buzzer
Figure 115: Inverter Push-Pull Circuit For drive voltages greater than what can be provided by an IC, a transistor circuit can be made (Figure 116).
V+
RC
Buzzer
INV. 1 INV. 2 INV. 3 Rb
R2
R1
C
Figure 116: External Drive Circuit Using A Transistor
Rb and RC are both generally about 1k. By using a higher voltage, the diaphragm deflects more and a higher SPL can be achieved. A transistor push-pull circuit can also be made to further increase SPL (Figure 117). The transistors are biased as switches and a square wave is applied to the bases 180o out of phase. This will have the same effect as the inverter in the previous circuit, causing the element to deflect in both directions and increasing the SPL, but it can han-
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PZT Application Manual
dle voltages that would destroy an IC.
V+
Rb1
Rb2
Signal A
Buzzer
Signal B
Signal B = Signal A + 180o
Figure 117: External Drive Push-Pull Circuit
(1) Input Electrode
V+
R1
R3
(3) Metal Plate (Ground)
(2) Feedback Electrode
R2 Vi
12 Vo
3
Vf
Figure 118: Example of Self-Drive Circuit
For the self drive circuit in Figure 118, R1 is chosen so that the transistor bias point, VCE, is half of the supply voltage. The following equation is used for the other resistors:
VF = R2 + hie VO hfe × R3
Where: hie = input impedance of transistor hfe = current amplification
Booster Coils
It is possible to increase the SPL of a buzzer by about 3 - 6dB by replacing RC in Figure 116 and R3 in Figure 118 with an inductor. The higher SPL is a result of the resonance between the inductor and the element, which is capacitive. The value of the inductor is determined by the following equation at the frequency of operation:
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fosc = ---------1--------2 LC
Where: L = value of the inductor C = capacitance of the piezoelectric element
Generally, a suitable value is between 30mH and 60mH. When the booster coil is used with the self drive circuit in Figure 118, the other resistor values will probably need to be changed to ensure stable oscillation.
Circuit Design Considerations
· Driving Waveform The piezo elements may be driven with sinusoidal, pulsed, or square waves. A sine wave will cause the device to operate at a frequency lower than the resonant frequency with a lower SPL. This is due to the loss of energy through the lag time between peak deflections. A square wave will produce higher sound levels because of the near instantaneous rise and fall time. Clipping of sinusoidal waveforms can result in frequency instability and pulse and square waves will cause an increase in harmonic levels. A capacitor in parallel with the diaphragm can reduce the harmonics.
· DC Precautions Subjecting the ceramic elements to direct current can cause them to depolarize and stop working. For this reason, it is best to drive the buzzers with an A.C. signal that has a zero D.C. bias. Blocking capacitors are recommended to prevent a bias.
· High Voltage Precautions Voltages higher than those recommended can cause permanent damage to the ceramic even if applied for short durations. Significantly higher sound pressure levels will not be achieved by higher voltages before permanent damage is caused.
· Shock Mechanical impact on piezoelectric devices can generate high voltages that can seriously damage drive circuitry, therefore, diode protection is recommended.
· SPL Control It is not recommended to place a resistor in series with the power source since this may cause abnormal oscillation. If a resistor is essential in order to adjust the sound pressure then place a capacitor (about 1µF) in parallel with the buzzer (Figure 119).
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Buzzer
Figure 119: Capacitor Bypass of Buzzer
PZT Application Manual
· Washing Murata provides water-resistant components but will not guarantee that no water will penetrate the device. If water should get inside the component then it could cause silver migration between the terminals. This could short out the device and cause it to stop functioning. For this reason, Murata recommends that the parts not be washed. Murata can supply some components with tape covering the sound-emitting hole. This will make the component more water resistant for washing.
· Soldering A lead wire is required to apply voltage to the piezoelectric diaphragm. This wire should be as fine as possible because it acts as a load on the diaphragm, which restricts oscillation. When using a soldering iron, the optimum temperature for soldering the lead wire to a metal plate is 300oC for a few seconds. The optimum temperature for soldering the lead wire to the ceramic silver electrode is 300oC for 0.5 second or less.
Parts
Table 14 lists the series of buzzers offered by Murata.
Buzzer Series PKMC PKM
PKB VSB PKD 7BB, 7NB, 7SB
Description Surface mount external drive buzzer Self or external drive with no internal circuitry Requires AC Drive Signal. Internal circuitry included. Requires DC Voltage Speaker Elements capable of reproducing speech Electroacoustic transducer for telephones Buzzer elements
Table 14. Buzzer Series Description
Figure 120 shows an example of the general part numbering system used by Murata.
PKM 22 E PP - 4 001
Series Case Diameter DriveType LeadType Frequency Suffix for special
requirements
See list of
E = External Drive PP = Pins
available
S = Self Drive W= wires
series
Figure 120: Buzzer Part Number System
Parts that are on tape (for automatic insertion) will have a TF01 suffix. Currently this is only available with the PKM13EPY-4000-TF01. Parts that come with tape over the sound-emitting hole will also have a suffix. PKM series parts will have an "S" suffix. PKB series parts will have a "W" suffix. The PKB series also has epoxy around the base to help prevent water from getting into the drive circuitry. Currently only the following buzzers are available sealed for washing: PKM22EPP-4001S PKM17EPP-4001S PKM25SP-3701S PKB24SPC-3601W PKB30SPC-2001W PKB30SPC-3001W
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Table 15 lists the buzzers offered by Murata.
Part Number
PKMC16E-4000-TY PKM22EPP-4001 PKM22EP-2001 PKM35-4AO PKM17EW-2001 PKM13EPY-4002 PKM17EPP-4001 PKM11-4AO PKM25-6AO PKM25SP-3701 PKM24SP-3805 PKM11-6AO PKM29-3AO PKM37-2AO PKB24SPC-3601 PKB30SPC-2001 PKB30SPC-3001 PKB5-3AO PKB6-5AO VSB35EW-0701B VSB50EW-O3O1B VSB41D25-07ARO PKD17EW-01R PKD22EW-01R PKM33EP-1001 PKM34EW-1101C PKM44EW-1001C PKM44EP-0901 PKM17EPT-4001 PKM22EPT-2001 PKM30SPT-2001 7BB-20-6C 7BB-27-4C 7BB-35-3C 7BB-41-2C 7SB-34R7-3C 7SB-34R7-3C2 7BB-20-6CAO 7BB-27-4CAO 7BB-35-3CAO 7BB-41-2CAO 7BB-12-9 7BB-15-6 7BB-20-6
Oscillating Frequency (kHz) 4 4 2 4 2 4 4 4.096 6.8 3.7 3.8 6.5 3.4 2 3.6 2 2.7 2.8 4.7 0.6 - 20 0.25 - 20 0.5 - 20 0.3 - 3.4 0.3 - 3.4 1 1.1 1 1 4 2 2 6.3 4.6 2.8 2.2 3.3 3.1 6.3 4.6 2.8 2.2 9 6 6.3
Case Diameter (mm) 16 22 22 16.8 16.8 12.6 17 24 25 25 24 24 39 30 24 30.3 30.3 42 34 35 50 50 17 21.5 33 34.5 61 40.5 20 26.5 33.25 20 27 35 41 34.7 37.4 20 27 35 41 12 15 20
Case Thickness (mm) 2.7 7 11 4 7 6.9 7 4.5 7 7 11 4.5 20 10 9.7 17.7 17.7 14.5 13.5 1.7 2.5 2 2 2 7.5 9 14 13 7.5 7 7.7 0.42 0.54 0.53 0.63 0.5 0.5 0.42 0.54 0.53 0.53 0.22 0.22 0.42
Pins / Wires
P P P W W P P W P P P W P P P P P W W --------------------P W W P P P P W W W W W W W W W W W W W
Pin
Available
Spacing in Tape
(mm)
16
N
10
N
22
N
-----
N
-----
N
5
Y
10
N
-----
N
4 / 8.5 N
4 / 8.5 N
ANGLED N
-----
N
8 / 10.5 N
ANGLED N
15
N
15
N
15
N
-----
N
-----
N
-----
-----
-----
-----
-----
-----
-----
-----
-----
-----
ANGLED N
N
N
45
N
10
N
12.5
N
7.5 / 12.5 N
-----
N
-----
N
-----
N
-----
N
-----
N
-----
N
-----
N
-----
N
-----
N
-----
N
-----
N
-----
N
-----
N
Table 15. Murta Buzzer Products
External / Self Drive
E E E E E E E E S S S S S S E E E E E E E E E E E E E E E E S S S S S S S S S S S E E E
Flange Center (mm) ----------------------------29 ------------29 --------------------50 45 ------------------------40 52 ---------------------------------------------------------------------
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PZT Application Manual
7BB-27-4
4.6
27
0.54
W
7BB-35-3
2.8
35
0.53
W
7BB-41-2
2.2
41
0.63
W
7SB-20-7
7.2
20
0.42
W
7SB-21-7
6.6
21
0.36
W
7SB-27-5
4.8
27
0.47
W
7BB-20-6AO
6.3
20
0.42
W
7BB-27-4AO
4.6
27
0.54
W
7BB-35-3AO
2.8
35
0.54
W
7BB-41-2A0
2.2
41
0.64
W
7NB-31R2-19R7DM-1 1.3
31.2
0.27
W
7NB-41-25DM-1
0.85
41
0.21
W
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
-----
N
E
-----
Table 15. Murta Buzzer Products
PZT Application Manual
Page 103
Appendix I
Equivalent Circuit Values
The following equivalent circuit values are for the circuit model in Figure 121.
C1
L1
R1
Co
Figure 121: Equivalent Circuit Model For Ceramic Resonator
Ceralok Type CSB400P CSB455E CSB500E CSB600P CSB700J CSB1000J CSB1200J
CSB456F11 CSB456F14 CSB500F2 CSB500F9 CSB503F2 CSB912JF103 CSB912JF104 CSKCC455E CSA2.00MG CSA2.50MG CSA3.00MG CSA3.58MG CSA4.00MG CSA4.19MG CSA5.00MG CSA6.00MG CSTS0400MG03 CSTS0358MG03 CSTS0500MG03 CSTS0600MG03 CSTS0800MG03
Fr (kHz) 388.5 443.9 487.2 586.5 682 978.5 1179.6 436.6 435.9 506.1 489 509.5 851.8 853 451.3 1922.9 2391.4 2856.1 3424.5 3812.8 4008 4801.3 5750.8 3372.5 3818 4757.5 5760 7667.5
Fa (kHz) 402.4 457.3 503.2 604.2 706.5 1013.3 1220.8 457.9 457.4 549.8 543.9 554 920.7 925.3 459.5 2046.7 2575 3083.5 3670.2 4118.6 4310.4 5133.6 6176.7 3722.5 4138 5190 6305 8282.5
R1 () 6.2 10.1 8.5 11.8 11.1 13.7 45.4 11.4 11 8.5 27.9 8.5 23.1 20.7
144.5 18.3 17.3 12.9 6.7 6.8 5.1 4.9 5.6 8.6 10.8 8.2 7.5 8.5
L1 (mH) 6.704 7.68 7.163 6.186 5.387 4.441 4.533 4.163 3.947 1.321 0.909 1.246 1.344 1.247 46.912 1.397 0.755 0.439 0.361 0.284 0.266 0.217 0.154 0.474 0.534 0.34 0.227 0.137
C1(pF) 25.046 16.74 14.907 11.912 10.068 5.958 4.018 31.924 33.785 74.896 116.569 78.33 25.971 27.909 2.651 4.908 5.867 7.073 5.993 6.125 5.948 5.046 4.987 4.694 3.254 3.288 3.367 3.147
Table 16. Resonator Equivalent Circuit Values
Co (pF) 344.364 272.76 222.824 194.269 146.862 82.481 56.489 320.378 333.517 415.585 490.913 429.017 154.401 157.875 72.895 36.942 36.786 42.741 40.324 36.719 37.978 35.692 32.469
21.5 18.63 17.296 16.991 18.863
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PZT Application Manual
CSTC2.00MG CSTC2.50MG CSTC3.00MG CSTCC3.58MG CSTCC4.00MG CSTCC5.00MG CSTCC6.00MG CSTCC8.00MG CSTCC10.0MG CSA8.00MTZ CSA10.0MTZ CSA11.0MTZ CSA12.0MTZ CSACV10.0MTJ CSACV12.0MTJ CSA16.00MXZ040 CSA20.00MXZ040 CSA27.00MXZ040 CSA30.00MXZ040 CSA33.86MXZ040 CSA40.00MXZ040 CSA50.00MXZ040 CSA60.00MXZ040 CSACV16.00MXJ040 CSACV20.00MXJ040 CSACV27.00MXJ040 CSACV30.00MXJ040 CSACV33.86MXJ040 CSACV40.00MXJ040 CSACV50.00MXJ040 CSACV60.00MXJ040 CSACW1600MX03 CSACW2000MX03 CSACW2700MX03 CSACW3386MX03 CSACW4000MX03 CSACW5000MX03
1950.6
2098
94.9
2433.9
2638
75
2877.5
3098.9
10
3488.7
3723.2
38
3796
4166
8.6
4746.8
5100
13.4
5725
6250
9.9
7585
8340
6.9
9530
10465
6.3
7650.9
8247.6
4.5
9628.7
10357.2
4.6
10586.9
11403.8
5.3
11511.2
12348.5
5.8
9539.3
10102.9
6.3
11408.1
12107.3
5.3
15966.7
16067.4
14.2
19929.6
20055.3
13.3
26930.8
27087.1
14.8
29893.1
30060.8
12.7
33766.3
33921.1
15.1
39932.2
40090.8
15.1
49918.6
50102.6
15.8
59973
60190
26.7
15934.1
16030.1
14.4
19957.8
20073.4
13.5
26916.8
27066.2
13.6
29912.3
30069.8
12.6
33779.2
33952.9
11.7
39917.8
40112.5
14.3
49903.4
50127
15.1
59913
60216.4
23
15962.8
16026.7
86.4
19955.2
20042.3
32.7
26952.3
27026.8
19
33822.6
33914.2
16.3
39913.5
40037.1
13.9
49949.6
50083.1
16.4
4.651 2.095 0.779 2.072 0.476 0.358 0.232 0.111 0.081 0.068 0.054 0.043 0.034 0.061 0.035 0.564 0.493 0.407 0.31 0.26 0.216 0.143 0.128 0.651 0.471 0.315 0.272 0.213 0.217 0.169 0.164 1.069 0.629 0.364 0.253 0.217 0.177
1.431 2.021 3.931 1.014 3.689 3.144 3.326 3.969 3.459 6.419 5.074 5.245 5.603 4.565 5.499 0.176 0.129 0.086 0.091 0.085 0.073 0.071 0.055 0.153 0.135 0.111 0.104 0.104 0.073 0.059 0.043 0.093 0.101 0.096 0.088 0.072 0.056
Table 16. Resonator Equivalent Circuit Values
9.124 11.612 24.598 7.228 18.045 20.37 17.337 18.992 16.802
39.6 32.313 32.784 67.196 37.515 43.527 13.922 10.217 7.365 8.163 9.273 9.314 9.572 7.834 12.685 11.636 9.967 9.867 10.126 7.548
6.72 4.315 16.876 11.557 17.327 16.131 11.875 10.843
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Page 105
Appendix 2
Resonator Test Circuit Values
The following charts list the test circuit values for Murata's resonators. The values shaded gray are standard parts that are currently available. Other values of built-in load capacitors are only available if recommended by an IC characterization.
CL (pf)
15
30
47
100
Series
Frequency Range
PN Suffix
x00
x40
CSAC-MGC(A) 1.80 to 6.00 MHz
Sort IC
CD4069UBE
TC74HCU04
CSAC-MGCM(A)
VDD (V)
5
5
Rf (ohm)
1M
1M
Rd (ohm)
0
680
CSTC-MGA
2.00 to 3.49MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x00 CD4069UBE
5 1M 0
CSTCC-MG(A) 2.00 to 10.0 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x00 CD4069UBE
5 1M 0
xH6 TC74HCU04
5 1M 680
Series
Frequency Range
CL (pf)
22
30
100
PN Suffix
x00
x40
CSACV-MTJ 8.00 to 13.00 MHz
Sort IC
CD4069UBE TC74HCU04
VDD (V)
12
5
Rf (ohm)
1M
1M
Rd (ohm)
0
220
CSTCV-MTJ
(8.00 to 10.00 MHz) 10.01 to 13.00 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xC4 TC40H004P
5 1M 0
CSACS-MT(A)
6.01 to 13.00MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x00
x40
CD4069UBE TC74HCU04
12
5
1M
1M
0
220
CSTCS-MT(A)
6.01 to 13.00MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x00 CD4069UBE
12 1M 0
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PZT Application Manual
Series
Frequency Range 13.50 to 15.99 MHz
CL (pf)
5
15
22
30
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xH1
xH3
xH4
x40
TC74HCU04 TC74HCU04 TC74HCU04 TC74HCU04
3
3
3
5
1M
1M
1M
1M
100
0
0
0
16.00 to 17.99 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xC1 TC40H004P
5 1M 0
xC3 TC40H004P
5 1M 0
xC4 TC40H004P
5 1M 0
x40 TC74HCU04
5 1M 0
CSACV-MXJ CSTCV-MXJ
18.00 to 19.99 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xC1 TC40H004P
5 1M 0
xH3 TC74HCU04
5 1M 100
xH4 TC74HCU04
5 1M 100
x40 TC74HCU04
5 1M 0
20.00 to 25.99 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xH1
x40
xH4
TC74HCU04 TC74HCU04 TC74HCU04
5
5
5
1M
1M
4.7k
100
0
0
26.00 to 70.00 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x40
xH3
xH4
TC74HCU04 TC74HCU04 TC74HCU04
5
5
5
1M
10k
4.7k
0
0
0
14.74 to 17.99 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xH1
xH3
xH4
x40
TC74HCU04 TC74HCU04 TC74HCU04 TC74HCU04
3
3
3
5
1M
1M
1M
1M
470
220
150
0
18.00 to 19.99 MHz
CSACV-MXA-Q CSTCV-MXA-Q 20.00 to 25.99 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xH1
xH3
xH4
x40
TC74HCU04 TC74HCU04 TC74HCU04 TC74HCU04
5
5
5
5
1M
1M
1M
1M
0
100
100
0
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xH1
x40
xH4
TC74HCU04 TC74HCU04 TC74HCU04
5
5
5
1M
1M
4.7k
100
0
0
26.00 to 70.00 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x40
xH3
xH4
TC74HCU04 TC74HCU04 TC74HCU04
5
5
5
1M
10k
4.7k
0
0
0
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S eries
CS A CW -M X CS T CW -M X
Frequency Range 16.00 to 24.99 MHz
CL (pf)
5
15
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x1 TC74HCU04
3 33k 220
x3 TC74HCU04
5 1M 0
25.00 to 39.99 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x1 TC74HCU04
5 1M 0
x3 TC74HCU04
5 22k
0
40.00 to 70.00 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x1 TC74HCU04
5 1M 0
x3 TC74HCU04
5 4.7k
0
Series CSA-MG(A) CST-MG(A) CST-MGW(A)
CSTS-MG(A)
CL (pf)
15
30
47
100
Frequency Range
PN Suffix
x00
x40
1.80 to 6.30 MHz
Sort IC
CD4069UBE
TC74HCU04
VDD (V)
5
5
Rf (ohm)
1M
1M
Rd (ohm)
0
680
3.40 to 10.00 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x3 TC4069UBP
5 1M 0
x6 TC74HCU04
5 1M 680
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PZT Application Manual
Series CSA-MTZ(A) CST-MTW(A)
CSA-MXZ(A) CST-MXW(A)
Frequency Range
CL (pf)
5
PN Suffix
6.31 to 13.0 MHz
Sort IC
VDD (V)
Rf (ohm)
Rd (ohm)
15
22
30
100
x00
x40
CD4069UBE TC74HCU04
12
5
1M
1M
0
220
12.00 to 17.99 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xC1 TC40H004P
5 1M 0
xC3 TC40H004P
5 1M 0
xC4 TC40H004P
5 1M 0
x40 TC74HCU04
5 1M 0
18.00 to 19.99 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xC1 TC40H004P
5 1M 0
xH3 TC74HCU04
5 1M 100
xH4 TC74HCU04
5 1M 100
x40 TC74HCU04
5 1M 0
20.00 to 25.99 Mhz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
xH1
x40
xH4
xH5
TC74HCU04 TC74HCU04 TC74HCU04 TC74HCU04
5
5
5
5
1M
1M
4.7k
3.3k
100
0
0
0
26.00 to 60.00 MHz
PN Suffix Sort IC VDD (V) Rf (ohm) Rd (ohm)
x04
xH3
xH4
xH5
TC74HCU04 TC74HCU04 TC74HCU04 TC74HCU04
5
5
5
5
1M
10k
4.7k
3.3k
0
0
0
0
PZT Application Manual
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Appendix 3
IC Characterization for Ceramic Resonators
Introduction
Due to the number of variations in clock circuits found in today's microcontrollers, it is impossible to make a standard resonator that works with every one of the ICs. While much of the time an off the shelf resonator will work with a given IC's clock circuit (by "work" we mean stable oscillation and minimal frequency shift from the intended oscillation frequency), there are many cases were the resonator will: · not start to oscillate
· stop oscillating at high or low temperature · have sporadic or overtone oscillation · resulting oscillation frequency not be in expected tolerance.
Most of the problems above are due to incompatibility between the resonator, hook-up circuit, and the IC's clock circuit. This is not an indication that the resonator is defective in some way. Such incompatibilities become more of a concern in high reliability applications like airbag controllers, ABS controllers, Aircraft controls, and Medical applications.
These incompatibilities result from the fact that resonator manufacturers must pick a standard test circuit to be used in production to confirm initial oscillation frequency of the ceramic resonator. For Murata, we use the RCA CD4069UBE as the CMOS resonator test circuit, and the Toshiba TC74HCU04 or TC40H004P as the HCMOS resonator test circuit (called out by the "x40" suffix in the resonator part number). For the big picture, there are inherent differences between CMOS and HCMOS IC technology that require us to offer these three sorting options. But, within each technology (CMOS vs. HCMOS) there can be many variations in IC design and die shrink level, that cause the resonator incompatibility / oscillation difficulties.
What can we do
To over come these incompatibilities, Murata has chosen to take the route of IC characterization. Murata has a dedicated application engineering section, whose sole function is to perform IC characterizations between customer ICs and Murata ceramic resonators. By performing the IC characterization, we are able to solve most of the resonator incompatibility issues that arise. Many solutions are just minor changes to the hook-up circuit (like changing load capacitor values), or solutions can be as major as designing a custom resonator part. Either way, the recommendation will assure you of 100% operation for your IC (assuming no changes to the IC we characterize for you) and that all resonators will be shipped to the recommended resonator specification. Murata has been performing IC characterizations for many years and has a great deal of experience in doing the evaluations. Many IC makers looking to put resonator recommendations in their IC's databooks, come to Murata for recommendations on resonators for their ICs via the IC characterization process.
Important Points of the Characterization Service
· The service is provided free of charge. · The IC / resonator characterization is done with worst case resonator (per Murata specification).
· The customer gets the complete recommended hook up circuit between the IC and the resonator. The customer does not need to worry about how to hook up the resonator with the IC, since we have provided it.
· The customer is advised which specific Murata resonator they should use. · The characterization is performed with the IC over either the standard temperature range (-20C to +80C) or the
automotive temperature range (-40C to +125C). The customer is also advised about effects of variations in input supply voltage. This is very important for automotive applications. · The characterization can take into account frequency correlation issues resulting from differences between customer ICs and Murata's standard sorting circuit. · The customer gets a form report from Murata supporting the resonator / hook-up circuit recommendation. · Typical lead time for the characterization is 6 to 8 weeks. Due to the time involved in doing the characterization, it is important that this process occur early in the design stage.
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· The IC characterization is available to both direct and distribution customers.
Murata has made available via the Internet a listing of IC / resonator characterizations done in the past. This can be found at "http://www.murata.com/develop/index.htm".
Please be careful with recommendations from this web site. Many IC makers change IC's (like redesigns or change the process linewidth) that have a great impact on the characterization results. Most IC makers do not easily indicate via there part number if such changes have occurred. This could result in a characterization from the web not being accurate for currently available ICs even if they have the same part number. We recommend that all new resonator designins should have the IC characterization done to insure good operation.
This appendix contains a form to be filled out by the customer, sales rep, or distributor rep. This appendix also contains instructions that explain what additional information is needed for the IC characterization. Please use this included form on all new IC characterization requests to Murata, since it greatly lessens the time needed to process such requests. It also insures that all the important information needed will be supplied the first time around, preventing repeated requests to the customer for additional information.
What is needed from the customer for IC characterization
For IC characterizations, please provide the following: · 2 to 5 bulk IC samples or the actual production PC board with ICs Mounted on it (the PC board is preferred so that
* parasitic effects on the board can be taken into account)
· A top View Pin-Out Diagram for the package of the IC samples. · The supply voltage and tolerance that the IC will operate under in design. · The Murata resonator part number they want characterized with the IC samples · The temperature range that the resonator must operate over in the design.
Notes: 1. If you are using a PIC micro-controller from Microchip, please provide information on which oscillator mode (XT or
HS) you are using. If you can preprogram the oscillator mode on the IC samples, it will help speed up the evaluation process. If you can not preprogram the IC, it will take an additional 1 to 2 weeks to complete the evaluation.
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2. If providing IC samples on PC boards, please attach wires for the power supply & ground and mark the wires.
Complete the form attached, arrange the above needed items, and mail or pass the completed form and IC samples (and any other needed items) to a local Murata Sales Representative. If you are not sure who your local Murata sales representative is, please consult the Murata Web page at www.Murata.com. This web page will have a link to a rep locator page, that will find the Murata rep for your area. The Murata rep will send the package on to the appropriate Murata Product Manager.
Within 4 to 5 weeks, Murata will provide the Initial Recommendation Report. This report will confirm the basic Murata resonator part number that insures stable oscillation and start-up over given circuit conditions. The only item not covered by this Initial Recommendation is frequency correlation (see Note below on Frequency correlation) between the standard Murata sorting IC and the IC under characterization. Within 4 to 5 weeks after providing the Initial Recommendation Report, Murata will provide the final Formal Recommendation Report. This report will cover correlation frequency.
Note: Correlation Frequency. It is very common to see a repeatable frequency shift between resonators sorted with Murata's standard sorting circuit and the actual IC used in design. This is mainly due to the various clock oscillator designs and construction methods used in the IC industry. The following example demonstrates correlation frequency shift: a resonator sorted by Murata's standard production sorting circuit produces a resonator exactly at 4.000MHz. When this resonator is used with a different IC (not the Murata production sorting circuit) it oscillates at 3.98MHz. This is a 0.5% shift down. This difference between Murata's standard sorting circuit and the application IC's clock circuit is the correlation frequency shift. This correlation shift is not covered under the initial oscillation frequency specification for the resonator. This correlation frequency shift occurs with all resonators, regardless of resonator maker. ** If frequency tolerance is crucial to your design, Murata is able to compensate for such a correlation shift by custom production frequency sorting or by making a custom resonator. Please note on the Evaluation Form if the initial oscillation frequency is critical to your application.
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IC Evaluation Information Sheet
Resonator
(Please Print All Information)
Application Information
Application: (required) Estimated Annual Usage: (required) Production Start Date: (required) Production Location:
(required)
IC and Test Information
IC Maker: (required) IC Part Number: (required) Resonator Part Number: (required)
Supply Voltage: (example: 5V± 0.5%): (required, must state tolerance for voltage) Temperature Range: (required)
Number of IC samples or modules enclosed:
Current Customer Circuit Conditions:
(If available)
Can the circuit conditions be changed:
Customer Contact Information
Customer Name: (required)
Customer Contact Person:
(required) Customer Contact Phone Number: (required)
Customer Contact e-mail Address:
(If available) Sales Rep. Name and Office:
Feedback resistor (Rf) = Load capacitors (CL1 / CL2)
YES
NO
= (please circle one)
**Additional Comments or Requests (attach additional page if needed):
PZT Application Manual
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IC Characterization for Ceramic Discriminators
Introduction
Like resonators, discriminators are subject to the differences between ICs. However, these differences can affect discriminators more severely than resonators. Small differences in the characteristics of an IC can cause a large frequency shift in the discriminator that could cause a signal to be distorted or cut out completely. For this reason, Murata discriminators are IC specific, meaning that we have one discriminator for each IC.
What We Can Do
To resolve these incompatabilities, Murata performs IC characterizations to determine the discriminator characteristics required by each IC and the customer's application. Murata has a dedicated application engineering section whose sole function is to perform IC characterizations between customer ICs and Murata discriminators. Once the required characteristics are determined, a custom discriminator is produced and a part number is assigned that indicates the associated IC.
Important Points of the Characterization Service
· The service is provided free of charge · The IC / discriminator characterization is done with the worst case discriminator (per Murata specification) · The customer is provided with all external component values (LS and RP) · The customer is advised of the discriminator part number · The characterization is performed over the standard temperature range (-20C to +80C) · Typical lead time for the characterization is 6 to 8 weeks. For this reason, it is important to begin the characteriza-
tion early in the design stage. · The IC characterization is available to both direct and distribution customers.
Murata has made available via the Internet a listing of IC / discriminator characterizations done in the past. This can be found at "http://www.murata.com/develop/index.htm". This list is also available in Appendix 5, but it is only current at the time of publication.
This appendix contains a form to be filled out by the customer, sales rep, or distributor rep. This appendix also contains instructions that explain what additional information is needed for the IC characterization. Please use this included form on all new IC characterization requests to Murata, since it greatly lessens the time needed to process such requests. It also insures that all the important information needed will be supplied the first time around, preventing repeated requests to the customer for additional information.
What is needed from the customer
The service is much the same as the resonator characterization, but we require some additional information: · 2 to 5 bulk IC samples or the actual production PC board with ICs Mounted on it (the PC board is preferred so that
* parasitic effects on the board can be taken into account)
· A top View Pin-Out Diagram for the package of the IC samples. · The supply voltage and tolerance that the IC will operate under in design. · The Murata resonator part number they want characterized with the IC samples · The temperature range that the resonator must operate over in the design. · The 3dB bandwidth desired · The 3dB recovered audio voltage desired · The signal input level · The frequency deviation
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· The modulation frequency
Note: If providing IC samples on PC boards, please attach wires for the power supply & ground and mark the wires.
Complete the form attached, arrange the above needed items, and mail or pass the completed form and IC samples (and any other needed items) to a local Murata Sales Representative. If you are not sure who your local Murata sales representative is, please consult the Murata Web page at www.Murata.com. This web page will have a link to a rep locator page, that will find the Murata rep for your area. The Murata rep will send the package on to the appropriate Murata Product Manager.
The report will contain graphs of recovered audio voltage and total harmonic distortion for several values of RP, LS, C, VCC, and signal input level. It will also contain the recommended values for the performance that comes closest to the desired performance indicated on the Characterization Form.
PZT Application Manual
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IC Evaluation Information Sheet
Discriminator
(Please Print All Information)
Customer Information
Customer Name:
(required)
Application:
(required)
Estimated Annual Usage:
(required)
Production Start Date:
(required)
IC Information
IC Maker:
(required)
IC Part Number:
(required)
Discriminator Part Number:
(required)
Target 3dB Bandwidth: (example: + 100kHz) (required) Target 3dB Recovered Audio Voltage: (example: 100mV) (required) Signal Input Level: (example: 100dBu)
(required)
Frequency Deviation: (example: +75kHz)
(required)
Modulation Frequency: (example: 1kHz)
(required)
Supply Voltage: (example: 5V± 0.5%):
(required, must state tolerance for voltage)
Customer Contact Information
Company Name: (required)
Contact Name:
(required)
Contact Phone Number:
(required)
Sales Rep. Name and Office:
Number of IC samples enclosed: ___________________
**Additional Comments or Requests (attach additional page if needed):
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PZT Application Manual
Appendix 4
EIA-J Date Code System
The EIA-J date code system uses twenty-four letters, omitting I and O, to indicate the month when a product was made. This system works on a four year cycle. Capital letters are used for the first two years and lower case letters are used for the next two years. This system was started in 1977 and follows the table below.
Year
1977 1981 1985 1989 1993 1997 2001 2005
Month 1 2 3 4 5 6 7 8 9 10 11 12
Letter A B C D E F G H J K L M
Year
1978 1982 1986 1990 1994 1998 2002 2006
Month Letter Year Month Letter
1
N
1
a
2
P
2
b
3
Q
1979
3
c
4
R
1983
4
d
5
S
1987
5
e
6
T
1991
6
f
7
U
1995
7
g
8
V
1999
8
9
W
2003
9
j
10
X
2007
10
11
Y
11
12
Z
12
m
Table 17. EIA-J Date Code System
Year
1980 1984 1988 1992 1996 2000 2004 2008
Month 1 2 3 4 5 6 7 8 9 10 11 12
Letter n
r t u
PZT Application Manual
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Appendix 5
Discriminator Characterization List
The following tables list the discriminators offered by Murata and the ICs that they work with. Table 18 is a list of MHz discriminators by IC manufacturer, Table 19 is a list of MHz discriminators by discriminator part number, and Table 20 is a list of the kHz discriminators.
IC Manufacturer NEC
Panasonic Rohm
Sanyo
Sony
Toko Toshiba
Audio Application IC IC
µPC1391M AN7004 AN7006S
AN7007SU AN7232 BA1440 BA1448 BA4110 BA4220
BA4230AF BA4234L BA4240L LA1260 LA1805 LA1810 LA1816 LA1827 LA1830 LA1831 LA1832/M
LA1835/M LA1838/M
CX-20029
CX-20076 CXA1030P CXA1238 CXA1376AM CXA1538M/N/S CXA1611 TK14581
TA2003 TA2007N TA2008A/AN TA2022 TA2029 TA2046 TA2057 TA2099N TA2104F TA2111
Part Number CDA10.7MG56 CDA10.7MG11 CDA10.7MG14A CDA10.7MG13 CDA10.7MG53 CDA10.7MG19 CDA10.7MG60 CDA10.7MG66 CDA10.7MG41 CDA10.7MG5 CDA10.7MG4 CDA10.7MG67 CDA10.7MG7 CDA10.7MG26 CDA10.7MG22 CDA10.7MG15 CDA10.7MG83 CDA10.7MG37 CDA10.7MG43 CDA10.7MG46 CDACV10.7MG46 CDA10.7MG48 CDA10.7MG74 CDA10.7MG79 CDA10.7MG1 CDACV10.7MG1 CDA10.7MG2 CDA10.7MG12 CDA10.7MG1 CDA10.7MG54 CDA10.7MG69 CDA10.7MG75 CDA10.7MG62 CDA10.7MG31 CDA10.7MG33 CDA10.7MG45 CDA10.7MG50 CDA10.7MG36 CDA10.7MG58 CDA10.7MG57 CDA10.7MG82 CDA10.7MG80A CDA10.7MG77
Table 18. MHz Discriminators By IC Manufacturer
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PZT Application Manual
Samsung Motorola Philips
Siemens Telefunken
TA7130P TA7303 TA7640AP TA7765 TA8122AN/AF
TA8124P TA8132AN/AF
TA8186 KA2292 KA2295 KA2298 MC13156 MC13173 TBA120U TBA229-2 TEA5592 TEA5594 TEA5710 TEA5712T TEA5762/5757 TDA1576T U2501B U4313B U4490B
CDA10.7MG9 CDA10.7MG8 CDA10.7MG6 CDA10.7MG71 CDA10.7MG16 CDACV10.7MG16 CDA10.7MGF226 CDA10.7MG18 CDA10.7MG39 CDA10.7MG63 CDA10.7MG64 CDA10.7MG65 CDA10.7MG49 CDA10.7MG52 CDA10.7MG29 CDA10.7MG21A CDA10.7MG30 CDA10.7MG35 CDA10.7MG40 CDA10.7MG55 CDA10.7MG61 CDA10.7MG51 CDA10.7MG28 CDA10.7MG81 CDA10.7MG34V
Visual Application IC IC Manufacturer Hitachi
Mitsubishi
IC HA1129 HA11566NT M51316BP M51316P M51345FP M51346BP M51346P M51348FP
M51354AP M51362SP M51365SP M51496P M52007FP M52014SP M52018FP M52031FP M52034FP M52044FP M52311FP M52313SP M52314SP M52316SP M52318SP M52322FP M52335SP
Part Number CDSH(4.5/5.5/6.0/6.5)MC18K CDSH(4.5/5.5/6.0/6.5)ME46K CDSH(4.5/5.5/6.0/6.5)MC28K CDSH(4.5/5.5/6.0/6.5)MC23K CDSH(4.5/5.5/6.0/6.5)MC35K CDSH(4.5/5.5/6.0/6.5)ME19K CDSH(4.5/5.5/6.0/6.5)ME6K CDSH(4.5/5.5/6.0/6.5)MC30K CDSH(4.5/5.5/6.0/6.5)ME72K CDSH(4.5/5.5/6.0/6.5)MC22K CDSH(4.5/5.5/6.0/6.5)ME58K CDSH(4.5/5.5/6.0/6.5)MC29K CDSH(4.5/5.5/6.0/6.5)ME23K CDSH(4.5/5.5/6.0/6.5)ME70K CDSH(4.5/5.5/6.0/6.5)ME47K CDSH(4.5/5.5/6.0/6.5)MC41K CDSH(4.5/5.5/6.0/6.5)MC44K CDSH(4.5/5.5/6.0/6.5)ME44K CDSH(4.5/5.5/6.0/6.5)ME43K CDSH(4.5/5.5/6.0/6.5)ME52K CDSH(4.5/5.5/6.0/6.5)ME74K CDSH(4.5/5.5/6.0/6.5)ME61K CDSH(4.5/5.5/6.0/6.5)ME65K CDSH(4.5/5.5/6.0/6.5)ME60K CDSH(4.5/5.5/6.0/6.5)ME55K CDSH(4.5/5.5/6.0/6.5)ME67K
Table 18. MHz Discriminators By IC Manufacturer
PZT Application Manual
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Page 120
NEC Panasonic
Sanyo
Sony Toko Toshiba
M52339 M52395SP µPC1167C2 µPC1382C µPC1383C µPC1391H µPC1411CA µPC1414CA µPC1416G µPC1800CA AN5135NK AN5138NK AN5155K AN5176K AN5180NK
LA1150 LA1231N LA7520 LA7521 LA7530 LA7540 LA7541 LA7545 LA7550/7555 LA7575 LA7577 LA7650 LA7655 LA7670/7671 LA7680/7681 LA7685 LA7770 CX-20014 CXA1110AS CXA3067 TK10489N TK1048M TA1201N/AN TA1209F TA7146P TA7522 TA7678AP TA7680AP TA8646N TA8670F TA8680N TA8691 TA8701N
TA8721SN TA8825N TA8864N
CDSH(4.5/5.5/6.0/6.5)ME68K CDSH(4.5/5.5/6.0/6.5)ME76K CDSH(4.5/5.5/6.0/6.5)MC11K CDSH(4.5/5.5/6.0/6.5)MC20K CDSH(4.5/5.5/6.0/6.5)MC21K CDSH(4.5/5.5/6.0/6.5)MC19K CDSH(4.5/5.5/6.0/6.5)MC27K CDSH(4.5/5.5/6.0/6.5)MC42K CDSH(4.5/5.5/6.0/6.5)MC33K CDSH(4.5/5.5/6.0/6.5)ME29K CDSH(4.5/5.5/6.0/6.5)ME5K CDSH(4.5/5.5/6.0/6.5)ME17K CDSH(4.5/5.5/6.0/6.5)ME12K CDSH(4.5/5.5/6.0/6.5)ME62K CDSH(4.5/5.5/6.0/6.5)ME63K CDSH(4.5/5.5/6.0/6.5)ME31K CDSH(4.5/5.5/6.0/6.5)MC36K CDSH(4.5/5.5/6.0/6.5)MC24K CDSH(4.5/5.5/6.0/6.5)MC25K CDSH(4.5/5.5/6.0/6.5)MC26K CDSH(4.5/5.5/6.0/6.5)ME18K CDSH(4.5/5.5/6.0/6.5)ME16K CDSH(4.5/5.5/6.0/6.5)ME21K CDSH(4.5/5.5/6.0/6.5)ME20K CDSH(4.5/5.5/6.0/6.5)ME41K CDSH(4.5/5.5/6.0/6.5)ME49K CDSH(4.5/5.5/6.0/6.5)ME27K CDSH(4.5/5.5/6.0/6.5)ME28K CDSH(4.5/5.5/6.0/6.5)ME42K CDSH(4.5/5.5/6.0/6.5)ME35K CDSH(4.5/5.5/6.0/6.5)ME51K
CDA10.7MG23 CDSH(4.5/5.5/6.0/6.5)ME1K CDSH(4.5/5.5/6.0/6.5)ME30K
CDA10.7MG76 CDSH(4.5/5.5/6.0/6.5)ME64K CDSH(4.5/5.5/6.0/6.5)ME59K CDSH(4.5/5.5/6.0/6.5)ME71K
CDA10.7MA28 CDSH(4.5/5.5/6.0/6.5)MC15K CDSH(4.5/5.5/6.0/6.5)MC32K CDSH(4.5/5.5/6.0/6.5)ME3K CDSH(4.5/5.5/6.0/6.5)ME11K CDSH(4.5/5.5/6.0/6.5)MC40K CDSH(4.5/5.5/6.0/6.5)MC37K CDSH(4.5/5.5/6.0/6.5)ME34K CDSH(4.5/5.5/6.0/6.5)ME37K CDSH(4.5/5.5/6.0/6.5)MC38K CDSH(4.5/5.5/6.0/6.5)ME69K CDSH(4.5/5.5/6.0/6.5)MC39K CDSH(4.5/5.5/6.0/6.5)ME77K CDSH(4.5/5.5/6.0/6.5)ME50K CDSH(4.5/5.5/6.0/6.5)MC46K CDSH(4.5/5.5/6.0/6.5)MC47K
Table 18. MHz Discriminators By IC Manufacturer
PZT Application Manual
LG Samsung Motorola
Philips Siemens
Telefunken
GL3815 KA2244 KA2245 KA2268 KA2919 MC13055 MC1357 MC3356 NE604 TBA229-2 TDA2557 ULN2111A A224D TBA120S TBA120T TBA120U TBA129 TBA130-2 TBA229 TBA229-2 TBA4280 TBA750 TDA2460 TDA2546A TDA2555/2557 TDA2556 TDA3800GS TDA3827 TDA3857 TDA3858 TDA4282T TDA4481 TDA4503 TDA4504 TDA4940 TDA6160-2X TDA6160X TDA8192 TDA8222 TDA8305 U2840B U829B
CDSH(4.5/5.5/6.0/6.5)ME48K CDA(4.5/5.5/6.0/6.5)MG59V CDSH(4.5/5.5/6.0/6.5)ME79K CDSH(4.5/5.5/6.0/6.5)ME73K CDSH(4.5/5.5/6.0/6.5)ME75K CDSH(4.5/5.5/6.0/6.5)ME56K CDSH(4.5/5.5/6.0/6.5)MC14K CDSH(4.5/5.5/6.0/6.5)ME14K CDSH(4.5/5.5/6.0/6.5)ME38K CDA(4.5/5.5/6.0/6.5)MG21 CDA(4.5/5.5/6.0/6.5)MG24 CDSH(4.5/5.5/6.0/6.5)MC13K CDSH(4.5/5.5/6.0/6.5)MC43K CDSH(4.5/5.5/6.0/6.5)ME15K CDSH(4.5/5.5/6.0/6.5)MC10K CDSH(4.5/5.5/6.0/6.5)ME13K CDSH(4.5/5.5/6.0/6.5)ME8K CDSH(4.5/5.5/6.0/6.5)MC34K CDSH(4.5/5.5/6.0/6.5)ME9K CDSH(4.5/5.5/6.0/6.5)ME32K CDSH(4.5/5.5/6.0/6.5)MC17K CDSH(4.5/5.5/6.0/6.5)MC12K CDSH(4.5/5.5/6.0/6.5)ME33K CDSH(4.5/5.5/6.0/6.5)ME10K CDSH(4.5/5.5/6.0/6.5)ME25K CDSH(4.5/5.5/6.0/6.5)ME22K CDSH(4.5/5.5/6.0/6.5)ME24K CDSH(4.5/5.5/6.0/6.5)ME40K CDSH(4.5/5.5/6.0/6.5)ME54K CDSH(4.5/5.5/6.0/6.5)ME57K CDSH(4.5/5.5/6.0/6.5)MC31K CDSH(4.5/5.5/6.0/6.5)ME66K CDSH(4.5/5.5/6.0/6.5)ME7K CDSH(4.5/5.5/6.0/6.5)ME26K CDSH(4.5/5.5/6.0/6.5)MC16K CDA(4.5/5.5/6.0/6.5)MG44V CDA(4.5/5.5/6.0/6.5)MG38V CDSH(4.5/5.5/6.0/6.5)ME39K CDSH(4.5/5.5/6.0/6.5)ME53K CDSH(4.5/5.5/6.0/6.5)ME45K CDSH(4.5/5.5/6.0/6.5)MC45K CDA(4.5/5.5/6.0/6.5)MG25 CDSH(4.5/5.5/6.0/6.5)ME36K
Table 18. MHz Discriminators By IC Manufacturer
PZT Application Manual
Page 121
Part Number
CDSH(4.5/5.5/6.0/6.5)MC10K CDSH(4.5/5.5/6.0/6.5)MC11K CDSH(4.5/5.5/6.0/6.5)MC12K CDSH(4.5/5.5/6.0/6.5)MC13K CDSH(4.5/5.5/6.0/6.5)MC14K CDSH(4.5/5.5/6.0/6.5)MC15K CDSH(4.5/5.5/6.0/6.5)MC16K CDSH(4.5/5.5/6.0/6.5)MC17K CDSH(4.5/5.5/6.0/6.5)MC18K CDSH(4.5/5.5/6.0/6.5)MC19K CDSH(4.5/5.5/6.0/6.5)MC20K CDSH(4.5/5.5/6.0/6.5)MC21K CDSH(4.5/5.5/6.0/6.5)MC22K CDSH(4.5/5.5/6.0/6.5)MC23K CDSH(4.5/5.5/6.0/6.5)MC24K CDSH(4.5/5.5/6.0/6.5)MC25K CDSH(4.5/5.5/6.0/6.5)MC26K CDSH(4.5/5.5/6.0/6.5)MC27K CDSH(4.5/5.5/6.0/6.5)MC28K CDSH(4.5/5.5/6.0/6.5)MC29K CDSH(4.5/5.5/6.0/6.5)MC30K CDSH(4.5/5.5/6.0/6.5)MC31K CDSH(4.5/5.5/6.0/6.5)MC32K CDSH(4.5/5.5/6.0/6.5)MC33K CDSH(4.5/5.5/6.0/6.5)MC34K CDSH(4.5/5.5/6.0/6.5)MC35K CDSH(4.5/5.5/6.0/6.5)MC36K CDSH(4.5/5.5/6.0/6.5)MC37K CDSH(4.5/5.5/6.0/6.5)MC38K CDSH(4.5/5.5/6.0/6.5)MC39K CDSH(4.5/5.5/6.0/6.5)MC40K CDSH(4.5/5.5/6.0/6.5)MC41K CDSH(4.5/5.5/6.0/6.5)MC42K CDSH(4.5/5.5/6.0/6.5)MC43K CDSH(4.5/5.5/6.0/6.5)MC44K CDSH(4.5/5.5/6.0/6.5)MC45K CDSH(4.5/5.5/6.0/6.5)MC46K CDSH(4.5/5.5/6.0/6.5)MC47K
CDSH(4.5/5.5/6.0/6.5)ME1K CDSH(4.5/5.5/6.0/6.5)ME3K CDSH(4.5/5.5/6.0/6.5)ME5K CDSH(4.5/5.5/6.0/6.5)ME6K CDSH(4.5/5.5/6.0/6.5)ME7K CDSH(4.5/5.5/6.0/6.5)ME8K CDSH(4.5/5.5/6.0/6.5)ME9K CDSH(4.5/5.5/6.0/6.5)ME10K CDSH(4.5/5.5/6.0/6.5)ME11K CDSH(4.5/5.5/6.0/6.5)ME12K CDSH(4.5/5.5/6.0/6.5)ME13K
IC Manufacturer CDSH...MC Type
Siemens NEC
Siemens Philips Motorola Toshiba Siemens Siemens Hitachi NEC NEC NEC Mitsubishi Mitsubishi Sanyo Sanyo Sanyo NEC Mitsubishi Mitsubishi Mitsubishi Siemens Toshiba NEC Siemens Mitsubishi Sanyo Toshiba Toshiba Toshiba Toshiba Mitsubishi NEC Siemens Mitsubishi Telefunken Toshiba Toshiba CDSH...ME Type Sony Toshiba Panasonic Mitsubishi Siemens Siemens Siemens Siemens Toshiba Panasonic Siemens
IC
TBA120T µPC1167C2
TBA750 ULN2111A
MC1357 TA7146P TDA4940 TBA4280 HA1129 µPC1391H µPC1382C µPC1383C M51354AP M51316P LA7520 LA7521 LA7530 µPC1411CA M51316BP M51365SP M51348FP TDA4282T TA7522 µPC1416G TBA130-2 M51345FP LA1231N TA8670F TA8701N TA8721SN TA8646N M52018FP µPC1414CA
A224D M52031FP
U2840B TA8867F TA8867FA
CX-20014 TA7678AP AN5135NK M51346P TDA4503
TBA129 TBA229 TDA2546A TA7680AP AN5155K TBA120U
Table 19. MHz Discriminators By Part Number
Page 122
PZT Application Manual
CDSH(4.5/5.5/6.0/6.5)ME14K CDSH(4.5/5.5/6.0/6.5)ME15K CDSH(4.5/5.5/6.0/6.5)ME16K CDSH(4.5/5.5/6.0/6.5)ME17K CDSH(4.5/5.5/6.0/6.5)ME18K CDSH(4.5/5.5/6.0/6.5)ME19K CDSH(4.5/5.5/6.0/6.5)ME20K CDSH(4.5/5.5/6.0/6.5)ME21K CDSH(4.5/5.5/6.0/6.5)ME22K CDSH(4.5/5.5/6.0/6.5)ME23K CDSH(4.5/5.5/6.0/6.5)ME24K CDSH(4.5/5.5/6.0/6.5)ME25K CDSH(4.5/5.5/6.0/6.5)ME26K CDSH(4.5/5.5/6.0/6.5)ME27K CDSH(4.5/5.5/6.0/6.5)ME28K CDSH(4.5/5.5/6.0/6.5)ME29K CDSH(4.5/5.5/6.0/6.5)ME30K CDSH(4.5/5.5/6.0/6.5)ME31K CDSH(4.5/5.5/6.0/6.5)ME32K CDSH(4.5/5.5/6.0/6.5)ME33K CDSH(4.5/5.5/6.0/6.5)ME34K CDSH(4.5/5.5/6.0/6.5)ME35K CDSH(4.5/5.5/6.0/6.5)ME36K CDSH(4.5/5.5/6.0/6.5)ME37K CDSH(4.5/5.5/6.0/6.5)ME38K CDSH(4.5/5.5/6.0/6.5)ME39K CDSH(4.5/5.5/6.0/6.5)ME40K CDSH(4.5/5.5/6.0/6.5)ME41K CDSH(4.5/5.5/6.0/6.5)ME42K CDSH(4.5/5.5/6.0/6.5)ME43K CDSH(4.5/5.5/6.0/6.5)ME44K CDSH(4.5/5.5/6.0/6.5)ME45K CDSH(4.5/5.5/6.0/6.5)ME46K CDSH(4.5/5.5/6.0/6.5)ME47K CDSH(4.5/5.5/6.0/6.5)ME48K CDSH(4.5/5.5/6.0/6.5)ME49K CDSH(4.5/5.5/6.0/6.5)ME50K CDSH(4.5/5.5/6.0/6.5)ME51K CDSH(4.5/5.5/6.0/6.5)ME52K CDSH(4.5/5.5/6.0/6.5)ME53K CDSH(4.5/5.5/6.0/6.5)ME54K CDSH(4.5/5.5/6.0/6.5)ME55K CDSH(4.5/5.5/6.0/6.5)ME56K CDSH(4.5/5.5/6.0/6.5)ME57K CDSH(4.5/5.5/6.0/6.5)ME58K CDSH(4.5/5.5/6.0/6.5)ME59K CDSH(4.5/5.5/6.0/6.5)ME60K CDSH(4.5/5.5/6.0/6.5)ME61K CDSH(4.5/5.5/6.0/6.5)ME62K CDSH(4.5/5.5/6.0/6.5)ME63K CDSH(4.5/5.5/6.0/6.5)ME64K CDSH(4.5/5.5/6.0/6.5)ME65K CDSH(4.5/5.5/6.0/6.5)ME66K CDSH(4.5/5.5/6.0/6.5)ME67K
Motorola Siemens
Sanyo Panasonic
Sanyo Mitsubishi
Sanyo Sanyo Siemens Mitsubishi Siemens Siemens Siemens Sanyo Sanyo NEC Sony Sanyo Siemens Siemens Toshiba Sanyo Telefunken Toshiba Philips Siemens Siemens Sanyo Sanyo Mitsubishi Mitsubishi Siemens Hitachi Mitsubishi
LG Sanyo Toshiba Sanyo Mitsubishi Siemens Siemens Mitsubishi Motorola Siemens Mitsubishi Toko Mitsubishi Mitsubishi Panasonic Panasonic Toko Mitsubishi Siemens Mitsubishi
MC3356 TBA120S LA7541 AN5138NK LA7540 M51346BP LA7550/7555 LA7545 TDA2556 M51496P TDA3800GS TDA2555/2557 TDA4505
LA650 LA7655 µPC1800CA CXA1110AS LA1150 TBA229-2 TDA2460 TA8680N LA7680/7681 U829B TA8691N NE604 TDA8192 TDA3827 LA7575 LA7670/7671 M52044FP M52034FP TDA8305 HA11566NT M52014SP GL3815 LA7577 TA8864N LA7685 M52311FP TDA8222 TDA3857 M52322FP MC13055 TDA3858 M51362SP TK1048M M52318SP M52314SP AN5176K AN5180NK TK10489N M52316SP TDA4481 M52335SP
Table 19. MHz Discriminators By Part Number
PZT Application Manual
Page 123
CDSH(4.5/5.5/6.0/6.5)ME68K CDSH(4.5/5.5/6.0/6.5)ME69K CDSH(4.5/5.5/6.0/6.5)ME70K CDSH(4.5/5.5/6.0/6.5)ME71K CDSH(4.5/5.5/6.0/6.5)ME72K CDSH(4.5/5.5/6.0/6.5)ME73K CDSH(4.5/5.5/6.0/6.5)ME74K CDSH(4.5/5.5/6.0/6.5)ME75K CDSH(4.5/5.5/6.0/6.5)ME76K CDSH(4.5/5.5/6.0/6.5)ME77K CDSH(4.5/5.5/6.0/6.5)ME79K CDSH(4.5/5.5/6.0/6.5)ME80B CDSH(4.5/5.5/6.0/6.5)ME81K
CDA(4.5/5.5/6.0/6.5)MG21 CDA(4.5/5.5/6.0/6.5)MG24 CDA(4.5/5.5/6.0/6.5)MG25 CDA(4.5/5.5/6.0/6.5)MG38V CDA(4.5/5.5/6.0/6.5)MG44V CDA(4.5/5.5/6.0/6.5)MG59V
CDA10.7MG1 CDA10.7MG1 CDA10.7MG2 CDA10.7MG4 CDA10.7MG5 CDA10.7MG6 CDA10.7MG7 CDA10.7MG8 CDA10.7MG9 CDA10.7MG11 CDA10.7MG12 CDA10.7MG13 CDA10.7MG14A CDA10.7MG15 CDA10.7MG16 CDA10.7MG18 CDA10.7MG19 CDA10.7MG21A CDA10.7MG22 CDA10.7MG23 CDA10.7MG26 CDA10.7MG28 CDA10.7MG29 CDA10.7MG30 CDA10.7MG31 CDA10.7MG33 CDA10.7MG34V CDA10.7MG35 CDA10.7MG36 CDA10.7MG37 CDA10.7MG39 CDA10.7MG40 CDA10.7MG41 CDA10.7MG43
Mitsubishi Toshiba Mitsubishi Toshiba Mitsubishi Samsung Mitsubishi Samsung Mitsubishi Toshiba Samsung Toshiba Sanyo CDA...MG Type Philips Philips Telefunken Siemens Siemens Samsung
Sony Sony Sony Rohm Rohm Toshiba Sanyo Toshiba Toshiba Panasonic Sony Panasonic Panasonic Sanyo Toshiba Toshiba Rohm Philips Sanyo Sanyo Sanyo Telefunken Philips Philips Toshiba Toshiba Telefunken Philips Toshiba Sanyo Toshiba Philips Rohm Sanyo
M52339 TA8701N M52007FP TA1201N/AN M51348FP KA2268 M52313SP KA2919 M52395SP TA8825N KA2245 TA31161 LA1150
TBA229-2 TDA2557
U829B TDA6160X TDA6160-2X
KA2244 CX-20029/20030
CXA1238 CX-20076 BA4234L BA4230AF TA7640AP
LA1260 TA7303P TA7130P AN7004 CXA1030P AN7007SU AN7006S LA1816 TA8122AN/AF TA8132AN/AF BA1440 TBA229-2 LA1810 LA7770 LA1805 U2501B TBA120U TEA5592 TA2003 TA2007N U4490B TEA5594 TA2029 LA1830 TA8186 TEA5710 BA4220 LA1831
Table 19. MHz Discriminators By Part Number
Page 124
PZT Application Manual
CDA10.7MG45 CDA10.7MG46 CDA10.7MG48 CDA10.7MG49 CDA10.7MG50 CDA10.7MG51 CDA10.7MG52 CDA10.7MG53 CDA10.7MG54 CDA10.7MG55 CDA10.7MG56 CDA10.7MG57 CDA10.7MG58 CDA10.7MG60 CDA10.7MG61 CDA10.7MG62 CDA10.7MG63 CDA10.7MG64 CDA10.7MG65 CDA10.7MG66 CDA10.7MG67 CDA10.7MG69 CDA10.7MG71 CDA10.7MG74 CDA10.7MG75 CDA10.7MG77 CDA10.7MG79 CDA10.7MG80A CDA10.7MG80 CDA10.7MG81 CDA10.7MG82 CDA10.7MG83 CDA10.7MG84 CDA10.7MG85 CDA10.7MG86 CDA10.7MG87 CDA10.7MG88
CDA10.7MA28
CDACV10.7MG1 CDACV10.7MG16 CDACV10.7MG46
Toshiba Sanyo Sanyo Motorola Toshiba CDB455CL13 Motorola Panasonic Sony Philips NEC Toshiba Toshiba Rohm Philips Toko Samsung Samsung Samsung Rohm Rohm Sony Toshiba Sanyo Sony Toshiba Sanyo Toshiba Toshiba Telefunken Toshiba Sanyo Rohm Philips Sanyo Motorola Toshiba CDA...MA Type Toshiba CDACV...MG Type Sony Toshiba Sanyo
TA2008A/AN LA1832/M LA1835/M MC13156 TA2022 TDA1576T MC13173 AN7232
CXA1376AM TEA5712T µPC1391M
TA2057 TA2046 BA1448 TEA5762/5757 TK14581 KA2292 KA2295 KA2298 BA4110 BA4240L CXA1538M/N/S TA7765 LA1838/M CXA1611 TA2111 LA1838/M TA2104F TA2104AFN U4313B TA2099N LA1827 BH4126FV SA639 LA1833 MC3363 TA8721ASN
TA1209F
CX-20029 TA8122AN
LA1832
Table 19. MHz Discriminators By Part Number
CDB Part Number CDB455C1
CDB455C3 CDB455C5
CDBM Part Number CDBM455C1 CDBM455C2 CDBM455C2 CDBM455C3 CDBM455C4 CDBM455C5
CDBC Part Number
CDBC455CX2 CDBC455CX2 CDBC455CX3
IC Manufacturer Siemens Toshiba Motorola Sony Sanyo NEC
Table 20. kHz Discriminator List
PZT Application Manual
IC S004 TA8104F MC3357 CXA1184M LA8610 PC1167C
Page 125
CDB455C7 CDB455C8 CDB455C9 CDB455CL9 CDB455C10 CDB455C11 CDB455C12 CDB455C13 CDB455C13A CDB455CL13 CDB455C14
CDB455C16 CDB455C17
CDB455C19 CDB455C21 CDB455CL21 CDB455C22
CDB455C24
CDB455C27 CDB455C28 CDB455C29
CDB455C30
CDB455C32
CDB455C34 CDB455C35
CDB455C38
CDB455C40
CDB455C42 CDB455C43 CDB455C44 CDB455C46 CDB455C47
CDB455C49 CDB455C50
CDB455C53 CDB455C54
CDBM455C7 CDBM455C8 CDBM455C9 CDBM455CL9 CDBM455C10
CDBM455C12
CDBM455C13A CDBM455CL13 CDBM455C14 CDBM455C15 CDBM455C16
CDBM455C18 CDBM455C20 CDBM45519 CDBM455C21 CDBM455CL21
CDBM455C23 CDBM455C24 CDBM455C25 CDBM455C26 CDBM455C27 CDBM455C28 CDBM455C29 CDBM455CL29 CDBM455C30 CDBM455C31 CDBM455C32 CDBM455C33 CDBM455C34 CDBM455C35 CDBM455C36
CDBM455C39 CDBM455C40 CDBM455C41 CDBM455C42 CDBM455C43
CDBM455C46 CDBM455C47 CDBM455C48 CDBM455C49 CDBM455C50 CDBM455C51 CDBM455C52 CDBM455C53 CDBM455C54
CDBC455CX7
CDBC455CX9 CDBC455CLX9
CDBC455CX13A CDBC455CLX13
CDBC455CX16
CDBC455CX19 CDBC455CX21 CDBC455CXL21
CDBC455CX24
CDBC455CX27 CDBC455CX28 CDBC455CX29 CDBC455CLX29 CDBC455CX30 CDBC455CX31 CDBC455CX32 CDBC455CX33
CDBC455CX35 CDBC455CX36 CDBC455CX37
CDBC455CX39 CDBC455CX40 CDBC455CX41 CDBC455CX42 CDBC455CX43
CDBC455CX46 CDBC455CX47 CDBC455CX48 CDBC455CX49 CDBC455CX50
CDBC455CX52 CDBC455CX53 CDBC455CX54
Motorola Siemens Philips Philips Toshiba Siemens Plessy
Sony Sony Sony Plessy Sony Motorola Plessy Motorola Toshiba Matsushita Toshiba Toshiba Sanyo Toshiba Toshiba Sony JRC Toko Toshiba Philips Philips Toko Toshiba Toshiba Sony Motorola Toko Philips Hitachi Lucent Philips Toshiba Matsushita Toko Sony Plessy NEC Toshiba Motorola Motorola Sony Toshiba Philips Sanyo Toshiba
Table 20. kHz Discriminator List
MC3357 TDA1576S1
NE604 NE604 TA8103F S1469 SL6652 CXA1003BM CXA1003AM/BM CXA1003AM/BM SL6654 CXA1183M MC3372 SL6655 MC3371 TA8104F AN6436S TA31132F TA31132F LA8604M TA7761F TA31136F CXA1484N NJM2232A TK10487 TA31142F NE605 NE605 TK14501 TA31141 TA31143F CXA1474 MC13136 TK10930 NE606/616 HA16841 W2005 SA607/617 TA31145 AN6159FA TK14590V/14591V CXA1683M SL6659 KC7357 TA31147 MC13110 MC3361 CXA3117N TA8104F SA625 LA8608V TA31149
Page 126
PZT Application Manual
Appendix 6
Internal Elements of Murata's Encased Buzzers
Table 21 lists the buzzer elements that are inside Murata's encased buzzers.
PZT Application Manual
Part Number
Internal Element
External Drive
PKM11-4A0
7BB-20-6-3
PKM13EPY-4000-TF01
7NB-11-9
PKM13EPY-4002
7NB-11-9
PKM17EPP-4001
7BB-15-5
PKM17EW-2001
6NB-15-10DM-3
PKM22EP-2001
7BB-20-4
PKM22EPP-2001
7BB-20-3
PKM22EPP-4001
7BB-20-6-1
PKM22EPP-4005
7BB-20-6-1
PKM22EPP-4007
7BB-20-6-1
PKM35-4A0
7BB-15-6-2
Self Drive
PKM11-6A0
7BB-20-6
PKM24SP-3805
7NB-21-4C-2
PKM25-6A0
7SB-21-7C
PKM29-3A0
7SB-34R7-3C
Internal Circuit
PKB24SPC-3601
7NB-21-4C-1
PKB24SW-3301
7NB-21-3C
PKB30SPC-2001
7NB-27-3C-3
PKB30SPC-3001
7NB-27-3C-2
PKB5-3A0
7BB-35-3R1C
PKB6-5A0
7BB-27-4C
Speaker
VSB35EW-0701B
PMGB0252-01
VSB50EW-0301B
PMGB0242-01
Receiver
PKD17EW-01R
6NB-16R3G-12DM-2
PKD22EW-01R
6NB-19R4-14DM-2R2
PKD33EW-01R
6NB-31R2-1R6
Ringer
PKM33EP-1201C
7NB-31R2-1
PKM34EW-1101C
7NB-31R2-1
PKM34EW-1201C
7NB-31R2-1R4
PKM44EP-0901
7NB-41-25DM-1
PKM44EW-1001C
7NB-41-1
Special Application
PKM17EPT-4001
7BB-15-6
PKM22EPT-2001
7BB-20-3
PKM22EPT-4001
7BB-20-6
PKM30SPT-2001
7NB-27-2C-3
Table 21. Encased Buzzer Internal Elements
Page 127
PKM30SPT-2501
7NB-27-2R7C-1
SMD Buzzer
PKMC16E-4000-TY
7NB-14R1-14R1-4
Table 21. Encased Buzzer Internal Elements
Page 128
PZT Application Manual
Appendix 7
Piezo Products Taping Lists
The following table lists the taping suffix and minimium order quantities for Murata's piezo products.
Bulk Part Number
Taping/Magazine Part Number
Quantity/Unit
Bulk
Taping/ Magazine
kHz Ceramic Resonators
Non-washable Type (Magazine)
CSB...P (375 - 429kHz)
CSB...P-CA01
500
50
CSB...E (430 - 509kHz)
CSB...E-CA01
500
50
CSB...P (510 - 699kHz)
CSB...P-CA01
500
50
CSU...P (450 - 500kHz)
CSU...P-CA01
500
50
Washable* Type (Magazine)
CSB...D (190 - 374kHz)
Not Available
100
------
CSB...J (375 - 699kHz)
CSB...J-CA01
500
50
CSB...J (700 - 1250kHz)
CSB...J-CA01
1000
100
Surface Mount (Taping)
CSBF...J (430 - 500kHz)
CSBF...J-TC01
------ 1500
CSKCC...E (400 - 600kHz)
CSKCC...E-TC01 ------
CSBF...J (700 - 1250kHz)
CSBF...J-TC01
------ 3000
MHz Ceramic Resonators
Leaded
2-Lead Terminal Type
CSA...MK(1.251 - 1.799MHz)
Not Available
500
------
CSA...MG (1.80 - 2.44MHz)
CSA...MG-TF01
500
1000
CSA...MG (2.45 - 6.30MHz)
CSA...MG-TF01
500
1500
CSA...MTZ (6.31 - 13.00MHz)
CSA...MTZ-TF01
500
1500
CSA...MXZ (13.01 - 60.00MHz)
CSA...MXZ-TF01
500
1500
CSALS..M...X-B0 (16.00 - 70.00MHz) CSTLS..M...X-A0
500
2000
Built-in Load Capacitor Type
CST...MG (1.80 - 2.44MHz)
CST...MG-TF01
500
1000
CST...MGW (2.45 - 6.30MHz)
CST...MGW-TF01
500
1500
CSTLS..M...G-B0 (2.00 - 3.39MHz) CSTLS..M...G-A0
500
2000
CSTS...MG (3.40 - 10.00MHz)
CSTS...MG-TZ
500
1500
CST...MTW (6.31 - 13.00)
CST...MTW-TF01
500
1000
CST...MXW (13.01 - 60.00MHz)
CST...MXW-TF01
500
1000
CSTLS..M...X-B0 (16.00 - 70.00MHz) CSTLS..M...X-A0
500
2000
Surface Mount
2-Lead Terminal Type
CSAC...MGC (1.80 - 6.00MHz)
CSAC...MGC-TC ------ 1500
CSAC...MGCM (1.80 - 6.00MHz)
CSAC...MGCM-TC ------
1500
CSACS...MT (6.01 - 13.00MHz)
CSACS...MT-TC
------ 1000
CSACV...MTJ (6.01 - 13.00MHz) CSACV...MTJ-TC20 ------ 2000
CSACS...MX (14.00 - 60.00MHz)
CSACS...MX-TC
------ 1000
CSACV...MXJ (13.50 - 70.00MHz) CSACV...MXJ-TC20 ------ 2000
Table 22. Piezo Products Taping List
Remarks
Built-in load capacitors
Obsolete Part
Washable* Obsolete Part
Washable*
Obsolete Part Deemphasized Part Deemphasized Part Deemphasized Part Deemphasized Part Deemphasized Part
Deemphasized Part Deemphasized Part
Washable* Washable* Standard from 10.01 - 13.00MHz Standard from 13.01 - 15.99MHz Washable*
Deemphasized Part Deemphasized Part Deemphasized Part Deemphasized Part Deemphasized Part Deemphasized Part
PZT Application Manual
Page 129
CSACW...MX (20.01 - 70.00MHz)
CSACW...MX03-T ------
3000
Deemphasized Part
Built-in Load Capacitor Type
CSTC...MG (2.00 - 3.50MHz)
CSTC...MG-TC20 ------ 2000
Obsolete Part
CSTCC...MG (2.00 - 10.00MHz)
CSTCC...MG-TC
------
2000
Standard from 2.00 - 3.99, 8.00 10.00MHz
CSTCR..M...G-B0 (4.00 - 7.99MHz) CSTCR..M...G-R0 ------ 3000
CSTCV...MTJ (10.01 - 13.00MHz) CSTCV...MTJ-TC20 ------ 2000
CSTCS...MX (14.00 - 60.00MHz)
CSTCS...MX-TC
------
1000
Deemphasized Part
CSTCV...MXJ (13.50 - 70.00MHz) CSTCV...MXJ-TC20 ------ 2000
CSTCW...MX (20.01 - 70.00MHz)
CSTCW...MX03-T ------ 3000
* Contact Murata for washing conditions
... represents the resonating frequency
kHz Filters
2nd IF Ladder Filters
CFU...[ ]2
CFU...[ ]2-CA01
200
50
4 Elements
CFWS...[ ]
CFWS...[ ]-CA01
150
50
6 Elements
CFV...[ ]
CFV...[ ]-CA01
150
50
7 Elements
CFUM...[ ]
Not Available
250
------
Miniature Size / 4 Elements
CFWM...[ ]
Not Available
150
------
Miniature Size / 6 Elements
CFVM...[ ]
Not Available
300
------
Miniature Size / 7 Elements
CFZM...[ ]
Not Available
150
------
Miniature Size / 9 Elements
CFUS...[ ]Y
CFUS...[ ]Y-CA01
200
50
CFWS...[ ]Y
Not Available
150
------
CFUM...[ ]Y
Not Available
250
------
CFWM...[ ]Y
Not Available
150
------
CFS...[ ]
Not Available
50
------
Metal Case / 15 Elements
CFK...[ ]
Not Available
80
------
Metal Case / 11 Elements
CFR...[ ]
Not Available
60
------
Metal Case / 11 Elements
CFX...[ ]
Not Available
150
------
Metal Case / 9 Elements
CFM...[ ]
Not Available
70
------
Metal Case / 9 Elements
CFG...[ ]
Not Available
150
------
Metal Case / 9 Elements
CFJ...K[ ]
Not Available
60
------
Metal Case / 11 Elements
CFKR...[ ]I
Not Available
80
------ Metal Case / 11 Elements / Flat GDT
CFL...[ ]G
Not Available
80
------ Metal Case / 9 Elements / Flat GDT
CFUCG...[ ]
CFUCG...[ ]-TC
------
450
SMD / 4 Elements
SFGCG...[ ]
SFGCG...[ ]-TC
------
450
SMD / 4 Elements
SFPC...[ ]
SFPC...[ ]-TC01
------ 1000
SMD / 4 Elements
CFUCH...[ ]
CFUCH...[ ]-TC
------
500
SMD / 4 Elements
CFZC...[ ]
CFZC...[ ]-TC
------
350
SMD / 8 Elements
CFWC...[ ]
CFWC...[ ]-TC
------
350
SMD / 6 Elements
... represents center frequency
[ ] represents the bandwidth code (A, B, C, D, E, F, G, H, I, J)
Discriminators
CDB...C[ ]
CDB...C[ ]-CA01
500
50
CDBM...C[ ]
CDBM...C[ ]-CA01 500
80
Miniature Version Of CDB
CDBC...CX[ ]
CDBC...CX[ ]-TC ------
500
SMD
... represents center frequency
[ ] represents IC indicator number
MHz Filters
SIF Filters
Table 22. Piezo Products Taping List
Page 130
PZT Application Manual
SFE...MB SFE...MC SFSL...MCB SFSL...MDB SFSL...MEB SFSH...MCB SFSH...MDB SFSH...MEB SFSRA...C SFSRA...D SFSRA...E SFT...MA SFSCC...MC
TPS...MJ TPS...MB TPS...MC TPS...MWA TPSRA...B-B0 TPSRA...C-B0 TPWA...B TPT...B TPSC...MB TPSC...MC MKT...MA
CDA...MC[ ] CDA...ME[ ] CDA...MG[ ] CDSL...MC[ ]K CDSL...ME[ ]K CDSH...MC[ ]K CDSH...ME[ ]K CDSC...MC[ ] CDAC...MC[ ] CDAC...MG[ ] CDACV...MG[ [
SAF...M[ ]80Z SAF...M[ ]70Z SAF...M[ ]60Z SAF...M[ ]55Z SAF...M[ ]200Z SAF...M[ ]220Z SAFW...M[ ]80Z
PZT Application Manual
SFE...MB-TF21
500
1500
SFE...MC-TF21
500
1500
Not Available
500
------
Not Available
500
------
Not Available
500
------
SFSH...MCB-TF21 500
1500
SFSH...MDB-TF21 500
1500
SFSH...MEB-TF21 500
1500
SFSRA...C-A0
500
2000
SFSRA...D-A0
500
2000
SFSRA...E-A0
500
2000
Not Available
250
1500
SFSCC...MC-TC10 ------ 3000
... represents center frequency
Trap Filters
TPS...MJ-TF23
500
1500
TPS...MB-TF21
500
1500
TPS...MC-TF21
500
1500
TPS...MWA-TF21
500
1500
TPSRA...B-A0
500
2000
TPSRA...C-A0
500
2000
TPWA...B-TF21
500
1500
TPT...B-TF21
500
1500
TPSC...MB-TC
500
2000
TPSC...MC-TC
500
2000
MKT...MA-TF01
500
1500
... represents center frequency
Discriminators
CDA...MC[ ]-TF21
500
1500
CDA...ME[ ]-TF21
500
1500
CDA...MG[ ]-TF21
500
1500
Not Available
500
------
Not Available
500
------
CDSH...MC[ ]K-TF21 500
1500
CDSH...ME[ ]K-TF21 500
1500
CDSC...MC[ ]-TC10 500
3000
CDAC...MC[ ]-TC ------ 1000
CDAC...MG[ ]-TC ------ 1000
CDACV...MG[ ]-TC ------ 2000
... represents center frequency
[ ] represents IC indicator number
SAW Filters
SAF...M[ ]80Z-TF01 300
500
Not Available
300
------
Not Available
300
------
Not Available
300
------
SAF...M[ ]200Z-TF01 300
500
SAF...M[ ]220Z-TF01 300
500
SAFW...M[ ]80Z-TF01 300
450
... represents center frequency
Table 22. Piezo Products Taping List
Discontinued
Double Trap Triple Trap
SMD SMD High Frequency Trap
SMD SMD SMD
Page 131
SFE...MA5-[ ] SFE...MS2-[ ] SFE...MS3-[ ] SFE...MA19-[ ] SFE...MA20-[ ] SFE...MA21-[ ] SFE...MA5A10-[ ] SFE...MS2A10-[ ] SFE...MS3A10-[ ] SFE...MJA10-[ ] SFE...MA5B10-[ ] SFE...MS2B10-[ ] SFE...MS3B10-[ ] SFE...MJB10-[ ] SFE...MHB10-[ ] SFE...MA5C10-[ ] SFE...MS2C10-[ ] SFE...MS3C10-[ ] SFE...MJC10-[ ] SFE...MHC10-[ ] SFE...MA8-[ ] SFE...MS2G-[ ] SFE...MS3G-[ ] SFE...MX-[ ] SFE...MZ-[ ] SFE...ML-[ ] SFE...MP-[ ] SFE...MM-[ ] SFE...MHY-[ ] SFE...MTE-[ ] SFE...MVE-[ ] SFE...MFP-[ ] SFT...MS3-[ ] SFT...MS2-[ ] SFT...MA5-[ ] SFECA...MA2-[ ] SFECA...MA5-[ ] SFECA...MS2-[ ] SFECA...MS3-[ ] SFECA...MJ-[ ] SFECA...MA19-[ ] SFECV...MA2S-[ ] SFECV...MA5S-[ ] SFECV...MS2S-[ ] SFECV...MS3S-[ ] SFECV...MJS-[ ] SFECV...MJKS-[ ] SFECV...MA19S-[ ]
Page 132
[ ] represents type
FM IF Filters
SFE...MA5-[ ]-TF21 500
SFE...MS2-[ ]-TF21 500
SFE...MS3-[ ]-TF21 500
SFE...MA19-[ ]-TF21 500
SFE...MA20-[ ]-TF21 500
SFE...MA21-[ ]-TF21 500
SFE...MA5A10-[ ]-TF21 500
SFE...MS2A10-[ ]-TF21 500
SFE...MS3A10-[ ]-TF21 500
SFE...MJA10-[ ]-TF21 500
SFE...MA5B10-[ ]-TF21 500
SFE...MS2B10-[ ]-TF21 500
SFE...MS3B10-[ ]-TF21 500
SFE...MJB10-[ ]-TF21 500
SFE...MHB10-[ ]-TF21 500
SFE...MA5C10-[ ]-TF21 500
SFE...MS2C10-[ ]-TF21 500
SFE...MS3C10-[ ]-TF21 500
SFE...MJC10-[ ]-TF21 500
SFE...MHC10-[ ]-TF21 500
SFE...MA8-[ ]-TF21 500
SFE...MS2G-[ ]-TF21 500
SFE...MS3G-[ ]-TF21 500
SFE...MX-[ ]-TF21 500
SFE...MZ-[ ]-TF21 500
SFE...ML-[ ]-TF21 500
SFE...MP-[ ]-TF21 500
SFE...MM-[ ]-TF21 500
SFE...MHY-[ ]-TF21 500
Not Available
500
Not Available
500
Not Available
500
Not Available
500
Not Available
500
Not Available
500
SFECA...MA2-[ ]-TC ------
SFECA...MA5-[ ]-TC ------
SFECA...MS2-[ ]-TC ------
SFECA...MS3-[ ]-TC ------
SFECA...MJ-[ ]-TC ------
SFECA...MA19-[ ]-TC ------
SFECV...MA2-[ ]-TC ------
SFECV...MA5-[ ]-TC ------
SFECV...MS2-[ ]-TC ------
SFECV...MS3-[ ]-TC ------
SFECV...MJ-[ ]-TC ------
SFECV...MJK-[ ]-TC ------
SFECV...MA19-[ ]-TC ------
1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 1500 ------------------------------2000 2000 2000 2000 2000 2000 2000 2000 2000 2000 2000 2000 2000
Table 22. Piezo Products Taping List
Wide Bandwidth Series Low Insertion Loss Series
High Attenuation Series
Low Profile Series
GDT Controlled Series GDT Improved Series
Narrow Bandwidth Type 2nd Harmonic Filter 2nd Harmonic Filter
Super Narrow Bandwidth Type 3 Element Series
PZT Application Manual
SFECV...MA21S-[ ] SFECV...MHS-[ ] SFECV...MHKS-[ ] SFECS...MA5-[ ] SFECS...MS2-[ ] SFECS...MS3-[ ] CFEC...M[*] CFECV...M[*] CFECS...M[*]
7BB-12-9 7BB-15-6 7BB-20-3 7BB-20-6 7BB-27-3 7BB-27-3R5 7BB-27-4 7BB-35-3 7BB-41-2 7BB-50M-1 7SB-20-7 7SB-27-5 7MB-15-11 7MB-20-7 7MB-27-3 7MB-27-4 7NB-31R2-19R7DM-1 7NB-35-1 7NB-41-25DM-1 7BB-20-6A0 7BB-27-4A0 7BB-35-3A0 7BB-41-2A0 7SB-20-7A1
7BB-20-6C 7BB-27-3C 7BB-27-4C 7BB-35-3C 7BB-41-2C 7SB-34R7-3C 7SB-34R7-3C2 7NB-27-2C 7NB-27-3C 7NB-27-4C 7BB-20-6CA0
PZT Application Manual
SFECV...MA21-[ ]-TC ------ 2000
SFECV...MH-[ ]-TC ------ 2000
SFECV...MHK-[ ]-TC ------ 2000
SFECS...MA5-[ ]-TC ------ 2000
SFECS...MS2-[ ]-TC ------ 2000
SFECS...MS3-[ ]-TC ------ 2000
CFEC...M[*]-TC
------ 2000
CFECV...M[*]-TC
------
2000
CFECS...M[*]-TC ------ 2000
... represents center frequency
[ ] represents rank of center frequency code
[*] represents type
Buzzers
External Drive Diaphragms
Not Available
5120 ------
Not Available
8000 ------
Not Available
3000 ------
Not Available
1800 ------
Not Available
1500 ------
Not Available
2400 ------
Not Available
1500 ------
Not Available
800
------
Not Available
400
------
Not Available
600
------
Not Available
1800 ------
Not Available
1500 ------
Not Available
------
Not Available
1800 ------
Not Available
1800 ------
Not Available
3500 ------
Not Available
1600 ------
Not Available
1200 ------
Not Available
1600 ------
Not Available
600
------
Not Available
600
------
Not Available
400
------
Not Available
250
------
Not Available
1600 ------
Self Drive Diaphragms
Not Available
1800 ------
Not Available
2400 ------
Not Available
1500 ------
Not Available
800
------
Not Available
400
------
Not Available
800
------
Not Available
800
------
Not Available
3000 ------
Not Available
1800 ------
Not Available
------
Not Available
600
------
Table 22. Piezo Products Taping List
Wide Bandwidth
Miniature version of the SFECV Miniature version of the SFECV Miniature version of the SFECV
GDT Controlled Version Of SFECV Miniature Version Of CFECV
Page 133
7BB-27-4CA0 7BB-35-3CA0 7BB-41-2CA0
PKM17EW-2001 PKM35-4A0 PKM11-4A0
PKM13EPY-4002 PKM17EPP-4001 PKM22EPP-2001 PKM22EPP-4001 PKM22EPP-4005 PKM22EPP-4007 PKM22EP-2001 PKM17EPT-4001 PKM22EPT-2001 PKM22EPT-4001 PKMC16E-4000
PKM11-6A0 PKM25-6A0 PKM29-3A0 PKM37-2A0 PKM25SP-3701 PKM24SP-3805 PKM30SPT-2001 PKM30SPT-2501
PKB24SW-3301 PKB6-5A0 PKB5-3A0
PKB24SPC-3601 PKB8-4A0
PKB30SPC-2001 PKB30SPC-3001
PKM34EW-1101C PKM34EW-1201C PKM44EW-1001C PKM44EP-0901 PKM33EP-1201C
PKD33EW-01R PKD22EW-01R
PKD17-01R
VSB41D25-07AR0 VSB35EW-0701B VSB50EW-0301B
Page 134
Not Available
600
------
Not Available
400
------
Not Available
250
------
External Drive Buzzers
Not Available
250
------
Not Available
500
------
Not Available
400
------
PKM13EPY-4002-TF01 330
500
Not Available
200
------
Not Available
750
------
Not Available
900
------
Not Available
750
------
Not Available
750
------
Not Available
360
------
Not Available
180
------
Not Available
300
------
Not Available
300
------
PKMC16E-4000-TY ------ 1200
Self Drive Buzzers
Not Available
400
------
Not Available
630
------
Not Available
90
------
Not Available
56
------
Not Available
130
------
Not Available
360
------
Not Available
70
------
Not Available
70
------
Buzzers With Internal Circuitry
Not Available
200
------
Not Available
25
------
Not Available
25
------
Not Available
650
------
Not Available
90
------
Not Available
80
------
Not Available
80
------
Ringers For Telephone Applications
Not Available
25
------
Not Available
25
------
Not Available
25
------
Not Available
160
------
Not Available
300
------
Receivers For Telephone Applications
Not Available
120
------
Not Available
300
------
Not Available
------
Speakers
Not Available
100
------
Not Available
160
------
Not Available
80
------
Table 22. Piezo Products Taping List
PZT Application Manual
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