CM Series/CM Radios Detailed Service Manual 6866545D30 O
User Manual: -CM Series/CM Radios Detailed service manual 6866545D30-O
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Commercial Series CM Radios Detailed Service Manual 6866545D30-O ii Commercial Series CM Radios Detailed Service Manual 6866545D30-O Contents Section 1 Service Maintainability Section 2 Controlhead Service Information Section 3 UHF2 Service Information Section 4 VHF2 Service Information Section 5 Midband Service Information Section 6 UHF2 High Power Service Information Section 7 VHF2 High Power Service Information WLS EMEA Publications Department, Jays Close, Viables Industrial Estate, Basingstoke, Hampshire, RG22 4PD, UK. Issue : December 2003 iii iv Commercial Series CM Radios Service Maintainability Issue: December 2003 ii Computer Software Copyrights The Motorola products described in this manual may include copyrighted Motorola computer programs stored in semiconductor memories or other media. Laws in the United States and other countries preserve for Motorola certain exclusive rights for copyrighted computer programs, including the exclusive right to copy or reproduce in any form, the copyrighted computer program. Accordingly, any copyrighted Motorola computer programs contained in the Motorola products described in this manual may not be copied or reproduced in any manner without the express written permission of Motorola. Furthermore, the purchase of Motorola products shall not be deemed to grant, either directly or by implication, estoppel or otherwise, any license under the copyrights, patents or patent applications of Motorola, except for the normal non-exclusive royalty-free license to use that arises by operation of law in the sale of a product. iii Table of Contents Chapter 1 INTRODUCTION 1.0 Scope of Manual ..................................................................................................1-1 2.0 Warranty and Service Support.............................................................................1-1 2.1 Warranty Period and Return Instructions .......................................................1-1 2.2 After Warranty Period .....................................................................................1-1 2.3 European Radio Support Centre (ERSC).......................................................1-2 2.4 Parts Identification and Ordering ....................................................................1-2 2.5 EMEA Test Equipment Support......................................................................1-2 2.6 Technical Support...........................................................................................1-3 2.7 Related Documents ........................................................................................1-3 3.0 Radio Model Information......................................................................................1-4 Chapter 2 MAINTENANCE 1.0 Introduction ..........................................................................................................2-1 2.0 Preventive Maintenance ......................................................................................2-1 2.1 Inspection .......................................................................................................2-1 2.2 Cleaning .........................................................................................................2-1 3.0 Safe Handling of CMOS and LDMOS..................................................................2-2 4.0 General Repair Procedures and Techniques.......................................................2-2 5.0 Notes For All Schematics and Circuit Boards ......................................................2-5 Chapter 3 SERVICE AIDS 1.0 Recommended Test Tools...................................................................................3-1 2.0 Test Equipment....................................................................................................3-2 iv v SAFETY INFORMATION Read this information before using your radio. PRODUCT SAFETY AND RF EXPOSURE FOR MOBILE TWO-WAY RADIOS INSTALLED IN VEHICLES OR AS FIXED SITE CONTROL STATIONS. This document provides information and instructions for the safe and efficient operation of Motorola Mobile Two-Way Radios. The information provided in this document supersedes information contained in user guides published prior to February 2002. COMPLIANCE WITH RF ENERGY EXPOSURE STANDARDS Note:This Radio is intended for use in occupational/controlled applications, where users have been made aware of the potential for exposure and can exercise control over their exposure. This radio device is NOT authorized for general population, consumer or similar use. This user safety booklet includes useful information about RF exposure and helpful instructions on how to control your RF exposures. Your Motorola radio is designed and tested to comply with a number of national and international standards and guidelines regarding human exposure to radio frequency electromagnetic energy. This radio complies with IEEE and ICNIRP exposure limits for occupational/controlled RF exposure environments at usage factors of up to 50% talk–50% listen. In terms of measuring RF energy for compliance with the IEEE/ICNIRP exposure guidelines, your radio radiates measurable RF energy only while it is transmitting (during talking), not when it is receiving (listening) or in standby mode. Your Motorola two-way radio complies with the following RF energy exposure standards and guidelines: ● ● ● ● ● ● ● United States Federal Communications Commission, Code of Federal Regulations; 47 CFR part 2 sub-part J American National Standards Institute (ANSI) / Institute of Electrical and Electronic Engineers (IEEE) C95. 1-1992 Institute of Electrical and Electronic Engineers (IEEE) C95.1-1999 Edition International Commission on Non-Ionizing Radiation Protection (ICNIRP) 1998 Ministry of Health (Canada) Safety Code 6. Limits of Human Exposure to Radiofrequency Electromagnetic Fields in the Frequency Range from 3 kHz to 300 GHz, 1999 Australian Communications Authority Radiocommunications (Electromagnetic Radiation - Human Exposure) Standard 2001 ANATEL, Brasil Regulatory Authority, Resolution 256 (April 11, 2001) “additional requirements for SMR, cellular and PCS product certification.” vi COMPLIANCE AND CONTROL GUIDELINES AND OPERATING INSTRUCTIONS FOR MOBILE TWO-WAY RADIOS INSTALLED IN VEHICLES To control your exposure and ensure compliance with the occupational/controlled environment exposure limits, always adhere to the following procedures: ● To transmit (talk), push the Push-To-Talk (PTT) button; to receive, release the PTT button. Transmit only when people outside the vehicle are at least the minimum lateral distance away from a properly installed, externally-mounted antenna. Table 1 lists the minimum distance for bystanders in an uncontrolled environment from the transmitting antenna at several different ranges of rated radio power for mobile radios installed in a vehicle.. Table 1: Rated Power and Distance ● Rated Power of Vehicle-Installed Mobile Two-Way Radio Minimum Distance from Transmitting Antenna Less than 7Watts 20 cm (8 Inches) 7 to 15 Watts 30.5 cm (1 Foot) 16 to 50 Watts 61 cm (2 Feet) 51 to 110 Watts 91.5 cm (3 Feet) Install mobile antennas at the centre of the roof and centre of the trunk deck. These mobile installation guidelines are limited to metal body vehicles. The antenna installation must additionally be in accordance with: a. The requirements of the antenna manufacturer/supplier ● b. Instructions in the Radio Installation Manual. Use only Motorola-approved supplied or replacement antenna. Use of non–Motorola - approved antennas, modifications, or attachments could damage the radio and may violate IEEE/ICNIRP regulations. For a list of Motorola-approved antennas please see your dealer. Your nearest dealer can be found at the following web site : http://www.motorola.com/cgiss/emea/dealerlocator.html For additional information on exposure requirements or other training information, visit http://www.motorola.com/rfhealth. COMPLIANCE AND CONTROL GUIDELINES AND OPERATING INSTRUCTIONS FOR MOBILE TWO-WAY RADIOS INSTALLED AS FIXED SITE CONTROL STATIONS If mobile radio equipment is installed at a fixed location and operated as a control station or as a fixed unit, the antenna installation must comply with the following requirements in order to ensure optimal performance and compliance with the RF energy exposure in the standards and guidelines listed above: ● ● The antenna must be mounted outside the building on the roof or a tower if at all possible. As with all fixed site antenna installations, it is the responsibility of the licensee to manage the site in accordance with applicable regulatory requirements and may require additional compliance actions such as site survey measurements, signage, and site access restrictions in order to insure that exposure limits are not exceeded. vii ELECTROMAGNETIC INTERFERENCE/COMPATIBILITY NOTE: Nearly every electronic device is susceptible to electromagnetic interference (EMI) if inadequately shielded, designed or otherwise configured for electromagnetic compatibility. It may be necessary to conduct compatibility testing to determine if any electronic equipment used in or around vehicles or near fixed site antenna is sensitive to external RF energy or if any procedures need to be followed to eliminate or mitigate the potential for interaction between the radio transmitter and the equipment or device. Facilities To avoid electromagnetic interference and/or compatibility conflicts, turn off your radio in any facility where posted notices instruct you to do so. Hospitals or health care facilities may be using equipment that is sensitive to external RF energy. Vehicles To avoid possible interaction between the radio transmitter and any vehicle electronic control modules, for example, ABS, engine, or transmission controls, the radio should be installed only by an experienced installer and that the following precautions be used when installing the radio: 1. Refer to the manufacturer’s instructions or other technical bulletins or recommendations on radio installation. 2. Before installing the radio, determine the location of the electronic control modules and their harnesses in the vehicle. 3. Route all radio wiring, including the antenna transmission line, as far away as possible from the electronic control units and associated wiring. Driver Safety Check the laws and regulations on the use of radios in the area where you drive. Always obey them. When using your radio while driving, please: ● ● Give full attention to driving and to the road. Pull off the road and park before making or answering a call if driving conditions so require. OPERATIONAL WARNINGS For Vehicles With An Air Bag Do not mount or place a mobile radio in the area over an air bag or in the air bag deployment area. Air bags inflate with great force. If a radio is placed in the air bag deployment area and the air bag inflates, the radio may be propelled with great force and cause serious injury to occupants of the vehicle. Potentially Explosive Atmospheres Turn off your radio prior to entering any area with a potentially explosive atmosphere. Sparks in a potentially explosive atmosphere can cause an explosion or fire resulting in bodily injury or even death. The areas with potentially explosive atmospheres referred to above include fuelling areas such as below decks on boats, fuel or chemical transfer or storage facilities, areas where the air contains chemicals or particles, such as grain, dust or metal powders. Areas with potentially explosive atmospheres are often but not always posted. Blasting Caps And Areas To avoid possible interference with blasting operations, turn off your radio when you are near electrical blasting caps, in a blasting area, or in areas posted: "Turn off two-way radio". Obey all signs and instructions. viii For radios installed in vehicles fueled by liquefied petroleum gas, refer to the (U.S.) National Fire Protection Association standard, NFPA 58, for storage, handling, and/or container information. For a copy of the LP-gas standard, NFPA 58, contact the National Fire Protection Association, One Battery Park, Quincy, MA. Chapter 1 INTRODUCTION 1.0 Scope of Manual This manual is intended for use by service technicians familiar with similar types of equipment. It contains service information required for the equipment described and is current as of the printing date. Changes which occur after the printing date may be incorporated by a complete Manual revision or alternatively as additions. NOTE Before operating or testing these units, please read the Safety Information Section in the front of this manual. 2.0 Warranty and Service Support Motorola offers long term support for its products. This support includes full exchange and/or repair of the product during the warranty period, and service/ repair or spare parts support out of warranty. Any "return for exchange" or "return for repair" by an authorised Motorola Dealer must be accompanied by a Warranty Claim Form. Warranty Claim Forms are obtained by contacting an Authorised Motorola Dealer. 2.1 Warranty Period and Return Instructions The terms and conditions of warranty are defined fully in the Motorola Dealer or Distributor or Reseller contract. These conditions may change from time to time and the following notes are for guidance purposes only. In instances where the product is covered under a "return for replacement" or "return for repair" warranty, a check of the product should be performed prior to shipping the unit back to Motorola. This is to ensure that the product has been correctly programmed or has not been subjected to damage outside the terms of the warranty. Prior to shipping any radio back to the appropriate Motorola warranty depot, please contact Customer Resources (Please see page 2 and page 3 in this Chapter). All returns must be accompanied by a Warranty Claim Form, available from your Customer Services representative. Products should be shipped back in the original packaging, or correctly packaged to ensure no damage occurs in transit. 2.2 After Warranty Period After the Warranty period, Motorola continues to support its products in two ways. 1. Motorola's Radio Aftermarket and Accessory Division (AAD) offers a repair service to both end users and dealers at competitive prices. 2. AAD supplies individual parts and modules that can be purchased by dealers who are technically capable of performing fault analysis and repair. 1-2 2.3 INTRODUCTION European Radio Support Centre (ERSC) The ERSC Customer Information Desk is available through the following service numbers: Austria: 08 00 29 75 41 Italy: 80 08 77 387 Belgium: 08 00 72 471 Luxemburg: 08 00 23 27 Denmark: 80 88 05 72 Netherlands: 08 00 22 45 13 Finland: 08 00 11 49 910 Norway: 80 01 11 15 France: 08 00 90 30 90 Portugal: 08 00 84 95 70 Germany: 08 00 18 75 240 Spain: 90 09 84 902 Greece: 00 80 04 91 29 020 Sweden: 02 07 94 307 UK : 08 00 96 90 95 Switzerland: 08 00 55 30 82 Ireland: 18 00 55 50 21 Iceland: 80 08 147 Or dial the European Repair and Service Centre: Tel: +49 30 6686 1555 Please use these numbers for repair enquiries only. 2.4 Piece Parts Some replacement parts, spare parts, and/or product information can be ordered directly. If a complete Motorola part number is assigned to the part, it is available from Motorola Radio Aftermarket and Accessory Division (AAD). If no part number is assigned, the part is not normally available from Motorola. If the part number is appended with an asterisk, the part is serviceable by Motorola Depot only. If a parts list is not included, this generally means that no user-serviceable parts are available for that kit or assembly. All part orders should be directed to : Motorola GmbH Customer Care AM Borsigturm 130 13507 Berlin Germany. 2.5 EMEA Test Equipment Support Information related to support and service of Motorola Test Equipment is available via Motorola Online (Extranet), through the Customer Care organisation of Motorola’s local area representation or by calling the the European Repair and Service Centre: Tel: +49 30 6686 1555 Warranty and Service Support 2.6 1-3 Technical Support Motorola Product Services is available to assist the dealer/distributors in resolving any malfunctions which may be encountered. UK/Ireland - Richard Russell Telephone: +44 (0) 1256 488 082 Fax: +44 01256 488 080 Email: BRR001@email.mot.com Central/East Europe - Siggy Punzenberger Telephone: +49 (0) 6128 70 2342 Fax: +49 (0) 6128 95 1096 Email: TFG003@email.mot.com Scandinavia Telephone: +46 8 735 9282 Fax: +46 8 735 9280 Email: C14749@email.mot.com Germany -Customer Connect Team Telephone: +49 (0) 6128 70 2248 Fax: +49 (0) 6128 95 1082 Email: cgiss.emea@europe.mot.com France - Lionel Lhermitte Telephone: +33 1 6929 5722 Fax: +33 1 6929 5904 Email: TXE037@email.mot.com Italy - Ugo Gentile Telephone: +39 0 2822 0325 Fax: +39 0 2822 0334 Email: C13864@email.mot.com Africa & Middle East - Armand Roy Telephone: +33 1 6929 5715 Fax: +33 1 6929 5778 Email: armand.roy@Motorola.com 2.7 Related Documents The following documents are directly related to the use and maintainability of this product. Title CM Series Product Manual Language Part Number English GMLN1062_ German GMLN1063_ French GMLN1064_ Italian GMLN1065_ Spanish GMLN1066_ Russian GMLN1067_ 1-4 3.0 INTRODUCTION Radio Model Information The model number and serial number are located on a label attached to the back of your radio. You can determine the RF output power, frequency band, protocols, and physical packages. The example below shows one mobile radio model number and its specific characteristics. Table 1-1 Radio Model Number (Example: MDM50FNC9AN2_N) Type of Model Unit Series M M = Mobile MD = Motorola Internal Use MD 50 Freq. Band Power Level Physical Packages Channel Spacing F Midband (6688MHz) J VHF1 (136162MHz) K VHF2 (146174MHz) N 1-25W C CM140 CM340 9 Programmable Q P UHF1 25-40W (403430MHz) F CM160 CM360 R Q UHF2 25-45W (438470MHz) S UHF3 (465495MHz) Protocol Feature Level Model Revision Model Package AA Conventional MDC 1 RF Connector : Mini-UHF A N AN 5 Tone 2 RF Connector : BNC Chapter 2 MAINTENANCE 1.0 Introduction This chapter of the manual describes: 2.0 ■ preventive maintenance ■ safe handling of CMOS devices ■ repair procedures and techniques Preventive Maintenance The radios do not require a scheduled preventive maintenance program; however, periodic visual inspection and cleaning is recommended. 2.1 Inspection Check that the external surfaces of the radio are clean, and that all external controls and switches are functional. It is not recommended to inspect the interior electronic circuitry. 2.2 Cleaning The following procedures describe the recommended cleaning agents and the methods to be used when cleaning the external and internal surfaces of the radio. External surfaces include the front cover, housing assembly, and battery case. These surfaces should be cleaned whenever a periodic visual inspection reveals the presence of smudges, grease, and/or grime. NOTE Internal surfaces should be cleaned only when the radio is disassembled for servicing or repair. The only recommended agent for cleaning the external radio surfaces is a 0.5% solution of a mild dishwashing detergent in water. The only factory recommended liquid for cleaning the printed circuit boards and their components is isopropyl alcohol (70% by volume). ! CAUTION: The effects of certain chemicals and their vapors can have harmful results on certain plastics. Aerosol sprays, tuner cleaners, and other chemicals should be avoided. 1. Cleaning External Plastic Surfaces The detergent-water solution should be applied sparingly with a stiff, non-metallic, shortbristled brush to work all loose dirt away from the radio. A soft, absorbent, lintless cloth or tissue should be used to remove the solution and dry the radio. Make sure that no water remains entrapped near the connectors, cracks, or crevices. 2. Cleaning Internal Circuit Boards and Components Isopropyl alcohol may be applied with a stiff, non-metallic, short-bristled brush to dislodge embedded or caked materials located in hard-to-reach areas. The brush stroke should direct the dislodged material out and away from the inside of the radio. Make sure that controls or tunable components are not soaked with alcohol. Do not use high-pressure air to hasten the drying process since this could cause the liquid to collect in unwanted places. Upon completion of the cleaning process, use a soft, absorbent, lintless cloth to dry the area. Do not brush or apply any isopropyl alcohol to the frame, front cover, or back cover. 2-2 MAINTENANCE NOTE 3.0 Always use a fresh supply of alcohol and a clean container to prevent contamination by dissolved material (from previous usage). Safe Handling of CMOS and LDMOS Complementary metal-oxide semiconductor (CMOS) devices are used in this family of radios. CMOS characteristics make them susceptible to damage by electrostatic or high voltage charges. Damage can be latent, resulting in failures occurring weeks or months later. Therefore, special precautions must be taken to prevent device damage during disassembly, troubleshooting, and repair. Handling precautions are mandatory for CMOS circuits and are especially important in low humidity conditions. DO NOT attempt to disassemble the radio without first referring to the CMOS CAUTION paragraph in the Disassembly and Reassembly section of the manual. 4.0 General Repair Procedures and Techniques IC Pre-Baking No pre-baking of components is required in the repair of this product. Parts Replacement and Substitution When damaged parts are replaced, identical parts should be used. If the identical replacement component is not locally available, check the parts list for the proper Motorola part number and order the component from the nearest Motorola Communications parts center listed in the “Piece Parts” section of this manual. Rigid Circuit Boards The family of radios uses bonded, multi-layer, printed circuit boards. Since the inner layers are not accessible, some special considerations are required when soldering and unsoldering components. The through-plated holes may interconnect multiple layers of the printed circuit. Therefore, care should be exercised to avoid pulling the plated circuit out of the hole. When soldering near the 18-pin and 40-pin connectors: ■ avoid accidentally getting solder in the connector. ■ be careful not to form solder bridges between the connector pins ■ closely examine your work for shorts due to solder bridges. General Repair Procedures and Techniques 2-3 Chip Components Use either the RLN4062 Hot-Air Repair Station or the Motorola 0180381B45 Repair Station for chip component replacement. When using the 0180381B45 Repair Station, select the TJ-65 minithermojet hand piece. On either unit, adjust the temperature control to 370 °C (700 °F), and adjust the airflow to a minimum setting. Airflow can vary due to component density. ■ ■ ■ To remove a chip component: 1. Use a hot-air hand piece and position the nozzle of the hand piece approximately 0.3 cm (1/8") above the component to be removed. 2. Begin applying the hot air. Once the solder reflows, remove the component using a pair of tweezers. 3. Using a solder wick and a soldering iron or a power desoldering station, remove the excess solder from the pads. To replace a chip component using a soldering iron: 1. Select the appropriate micro-tipped soldering iron and apply fresh solder to one of the solder pads. 2. Using a pair of tweezers, position the new chip component in place while heating the fresh solder. 3. Once solder wicks onto the new component, remove the heat from the solder. 4. Heat the remaining pad with the soldering iron and apply solder until it wicks to the component. If necessary, touch up the first side. All solder joints should be smooth and shiny. To replace a chip component using hot air: 1. Use the hot-air hand piece and reflow the solder on the solder pads to smooth it. 2. Apply a drop of solder paste flux to each pad. 3. Using a pair of tweezers, position the new component in place. 4. Position the hot-air hand piece approximately 0.3 cm (1/8” ) above the component and begin applying heat. 5. Once the solder wicks to the component, remove the heat and inspect the repair. All joints should be smooth and shiny. 2-4 MAINTENANCE Shields Removing and replacing shields will be done with the R1070 station with the temperature control set to approximately 215°C (415°F) [230°C (445°F) maximum]. ■ ■ To remove the shield: 1. Place the circuit board in the R1070 circuit board holder. 2. Select the proper heat focus head and attach it to the heater chimney. 3. Add solder paste flux around the base of the shield. 4. Position the shield under the heat-focus head. 5. Lower the vacuum tip and attach it to the shield by turning on the vacuum pump. 6. Lower the focus head until it is approximately 0.3 cm (1/8”) above the shield. 7. Turn on the heater and wait until the shield lifts off the circuit board. 8. Once the shield is off, turn off the heat, grab the part with a pair of tweezers, and turn off the vacuum pump. 9. Remove the circuit board from the R1070 circuit board holder. To replace the shield: 1. Add solder to the shield if necessary, using a micro-tipped soldering iron. 2. Next, rub the soldering iron tip along the edge of the shield to smooth out any excess solder. Use solder wick and a soldering iron to remove excess solder from the solder pads on the circuit board. 3. Place the circuit board back in the R1070 circuit board holder. 4. Place the shield on the circuit board using a pair of tweezers. 5. Position the heat-focus head over the shield and lower it to approximately 0.3 cm (1/8”) above the shield. 6. Turn on the heater and wait for the solder to reflow. 7. Once complete, turn off the heat, raise the heat-focus head and wait approximately one minute for the part to cool. 8. Remove the circuit board and inspect the repair. No cleaning should be necessary. Notes For All Schematics and Circuit Boards 5.0 2-5 Notes For All Schematics and Circuit Boards * Component is frequency sensitive. Refer to the Electrical Parts List for value and usage. 1. Unless otherwise stated, resistances are in Ohms (k = 1000), and capacitances are in picofarads (pF) or microfarads (µF). 2. DC voltages are measured from point indicated to chassis ground using a Motorola DC multimeter or equivalent. Transmitter measurements should be made with a 1.2 µH choke in series with the voltage probe to prevent circuit loading. 3. Interconnect Tie Point Legend: Signal Name Signal Description 16_8MHz 16.8MHz Reference Frequency from Synthesizer to ASFIC 3V 3V RF regulator 5V 5V RF regulator 5V_CH Optional 5V for Control Head 9V Regulated 9.3V Supply Voltage 9R 9V to enable RX_INJ when RX_EN is active ASFIC_CS ASFIC Chip Select B+ 13.8V Supply Voltage BATT_SENSE Battery Voltage Sense Line BOOT_EN_IN_CH Boot Mode Select BW_SEL Select BW (12.5 KHz, 25 KHz) CH_ACT Channel Activity Indicator Signal (Fast Squelch) COMM_DATA_SEL_CH Display Driver Command/ Data Select D3_V3 Regulated 3.3V supply voltage for Voice Storage DEMOD Audio Output Signal from the Receiver IC DETECTOR_AUDIO_SEND_BRD Flat Audio to Option Board DISPLAY_CS_CH Control Head Chip Select EMERGENCY_ACCES_CONN Emergency line to switch on the radio voltage regulators EMERGENCY_SENSE Emergency sense to µP EXTERNAL_MIC_AUDIO ACCES_CONN External (from accessory connector) microphone input F1200 Interrupt line from ASFIC CMP FILT_SW_B+ Switched 13.8 V supply voltage FLAT_TX_AUDIO_INPUT_ACCESS_CONN Flat TX input from accessory connector HANDSE RX_AUDIO_CH Handset Audio Output HOOK_CH Hang-up switch input HSIO High Speed Clock In / Data Out IGNITION Ignition Line to switch on he radio’s voltage regulator KEYPAD_COL_CH Keypad Matrix Column LOC_DIST Enable Attenuator for RX line LSIO Low Speed Clock In / Data Out MIC_AUDIO_CH Microphone Input 2-6 MAINTENANCE MIC_PTT_CH Microphone PTT Input MOD_IN Modulation Signal from ASFIC MOD_OUT Modulation Signal to the Synthesizer ONOFF_SENSE On off sense switch OPT_DATA_R_OPRD DATA/Ready Request from Option Board OPT_EN_OPBD Option Board Chip Select PA_BIAS PA Control bias voltage PA_CURRENT Not used POST_LIMITER_TX AUDIO_RETURN_OPT_BRD Flat TX Input from Option Board PROG x IN ACC y General Purpose Input x accessory connector Pin y PROG x INOUT ACC y General Purpose Input/Output x accessory connector Pin y PROG x OUT ACC y General Purpose Input x accessory connector Pin y PWR_SET PA Power Control Voltage RESET Reset Line RSSI Received Signal Strength Indicator RX RX signal RX AUD RTN Option Board Input/Output of Receiver Audio Path RX_AUDIO_OUTPUT_ACCESS_CONN Flat or filtered audio to accessory connector RX_EN Enable Receiving RX_INJ RF signal from VCO into the Receiver SCI_CH Bi-directional serial communication line SHIFT_R_CS SPI Chip select for the Control Head SPI_CLK Serial peripheral interface bus CLOCK SPI_MISO Serial peripheral interface bus data IN SPI_MOSI Serial peripheral interface bus data OUT SPKR- Negative Audio PA Speaker Output SPKR- Negative Audio PA Speaker Output SPKR+ Positive Audio PA Speaker Output SQ_DET Squelch Detect Signal SYNTH_CS Synth Chip Select SYNTH_LOCK µP Clock Lock Signal TX AUDIO_RETURN_OPT_BRD Option Board Output to Transmit Audio Path TX AUDIO_SEND_OPT_BRD Microphone Audio to Option Board TX_INJ RF signal from the VCO to transmitter PA TX_EN Enable transmitting UNMUTED RX_AUDIO_SEND_OPT_BRD Unmuted filtered audio to option board uP_CLK µP Clock signal VoL_INDIRECT Volume Pot Input VOX Voice operated transmit level Notes For All Schematics and Circuit Boards 2-7 VS AUDIO_SEL Switch signal to Enable option board audio output signal VS GAIN_SEL Voice Storage Gain Select line VS_MIC Voice Storage Audio Signal to microphone path VS_INT Voice Storage Interrupt line VS_RAC Voice storage Row Address Clock Signal VSTBY 3.3 V supply for µP when the radio is switched off 2-8 MAINTENANCE Chapter 3 SERVICE AIDS 1.0 Recommended Test Tools Table 3.1 lists the service aids recommended for working on the radio. While all of these items are available from Motorola, most are standard workshop equipment items, and any equivalent item capable of the same performance may be substituted for the item listed. Table 3-1 Service Aids Motorola Part No. Description Application RLN4460_ Portable Test Set Enables connection to audio/accessory jack. Allows switching for radio testing. GMVN5034_ Customer Programming Software (CPS) and Tuner CDROM (MDC) Programs customer options and channel data. Tunes hardware parameters, front end, power, deviation etc. GMVN5033_ Customer Programming Software (CPS) and Tuner CDROM (5-Tone) Programs customer options and channel data. Tunes hardware parameters, front end, power, deviation etc. RKN4081_ Programming Cable with Internal RIB Includes radio interface box (RIB) capability. FKN8096_ Data/Flash Adapter Key Used with RKN4081 (10 to 8 pin adapter for front Telco connector with Data/Flash switch). RKN4083_ Mobile Programming/Test Cable Connects radio to RIB (RLN4008_).via rear accessory connector FKN8113_ Adapter Cable Used with RKN4083 (20 to 16 pin adapter for rear accessory connector). GTF374_ Program Cable Connects RIB to Radio microphone input. RLN4008_ Radio Interface Box Enables communications between radio and computer’s serial communications adapter. HLN8027_ Mini UHF to BNC Adaptor Adapts radio antenna port to BNC cabling of test equipment. GPN6133_ Power Supply Provides the radio with power when bench testing. EPN4040_ Wall-Mounted Power Supply Used to supply power to the RIB (UK). EPN4041_ Wall-Mounted Power Supply Used to supply power to the RIB (Euro). 8180384N64 Housing Eliminator (25W) Test Fixture used to bench test the radio pcb. 3080369B71 Computer Interface Cable Connects the RIB to the Computer (25-pin). 3-2 SERVICE AIDS Table 3-1 Service Aids Motorola Part No. Description Application 3080369B72 Computer Interface Cable Connects the RIB to the Computer (9-pin) (Use for IBM PC AT - other IBM models use the B71 cable above). 6686119B01 Removal Tool Assists in the removal of radio control head. 6680334F39 Hex Tool Assists in the removal of antenna connector. WADN4055A Portable Soldering Station Digitally controlled soldering iron. 6604008K01 0.4mm Replacement Tip For WADN4055A Soldering iron. 6604008K01 0.8mm Replacement Tip For WADN4055A Soldering iron. 0180386A82 Anti-static Grounding Kit Used for all radio assembly/disassembly procedures. 6684253C72 Straight Prober 6680384A98 Brush 1010041A86 Solder (RMA type) 63/37, 0.5mm diameter, 1lb. spool. Test Equipment 2.0 3-3 Test Equipment Table 3-2 lists test equipment required to service the radio and other two-way radios. Table 3-2 Recommended Test Equipment Motorola Part No. Description Characteristics Application R2600_NT Comms System This monitor will Analyzer (non MPT) substitute for items with an asterisk * Frequency/deviation meter and signal generator for widerange troubleshooting and alignment *R1072_ Digital Multimeter AC/DC voltage and current measurements *R1377_ AC Voltmeter 100 µV to 300 V, 5Hz-1MHz, 10 Megohm input impedance Audio voltage measurements WADN4133 Delay Oscilloscope 2 Channel 40 MHz bandwidth, 5 mV/cm - 20 V/cm Waveform measurements R1440_ Wattmeter, Transmitter power output measurements 0180305F17 0180305F31 0180305F40 RLN4610_ Plug-in Elements Plug-in Elements Plug-in Elements Carry case Thruline 50-Ohm, ±5% accuracy 10W, 25 - 60 MHz 10W, 100 - 250 MHz 10W, 200 - 500 MHz Wattmeter and 6 elements T1013_ RF Dummy Load S1339_ RF Millivolt Meter 100mV to 3 VRF, 10 kHz to 1.2 GHz RF level measurements R1011_/220V 220V Power Supply 0-40V, 0-40A Programmable 3-4 SERVICE AIDS Commercial Series CM Radios Controlhead Service Information Issue: December 2003 ii Computer Software Copyrights The Motorola products described in this manual may include copyrighted Motorola computer programs stored in semiconductor memories or other media. Laws in the United States and other countries preserve for Motorola certain exclusive rights for copyrighted computer programs, including the exclusive right to copy or reproduce in any form, the copyrighted computer program. Accordingly, any copyrighted Motorola computer programs contained in the Motorola products described in this manual may not be copied or reproduced in any manner without the express written permission of Motorola. Furthermore, the purchase of Motorola products shall not be deemed to grant, either directly or by implication, estoppel or otherwise, any license under the copyrights, patents or patent applications of Motorola, except for the normal non-exclusive royaltyfree license to use that arises by operation of law in the sale of a product. iii Table of Contents Chapter 1 MODEL OVERVIEW 1.0 CM140/CM340 Models ........................................................................................1-1 2.0 CM160/CM360 Models ........................................................................................1-1 Chapter 2 THEORY OF OPERATION 1.0 Introduction ..........................................................................................................2-1 2.0 Controlhead Model for CM140 and CM340 .........................................................2-1 2.1 Power Supplies...............................................................................................2-1 2.2 Power On / Off................................................................................................2-1 2.3 Microprocessor Circuit....................................................................................2-1 2.4 SBEP Serial Interface.....................................................................................2-1 2.5 Keypad Keys ..................................................................................................2-1 2.6 Status LED and Back Light Circuit..................................................................2-3 2.7 Microphone Connector Signals ......................................................................2-3 2.8 Speaker ..........................................................................................................2-4 2.9 Electrostatic Transient Protection ...................................................................2-4 3.0 Controlhead Model for CM160 andCM360 ..........................................................2-4 3.1 Power Supplies...............................................................................................2-4 3.2 Power On / Off................................................................................................2-4 3.3 Microprocessor Circuit....................................................................................2-5 3.4 SBEP Serial Interface.....................................................................................2-5 3.5 Keypad Keys ..................................................................................................2-6 3.6 Status LED and Back Light Circuit..................................................................2-6 3.7 Liquid Crystal Display (LCD) ..........................................................................2-6 3.8 Microphone Connector Signals ......................................................................2-6 3.9 Speaker ..........................................................................................................2-7 3.10 Electrostatic Transient Protection ...................................................................2-8 Chapter 3 TROUBLESHOOTING CHARTS 1.0 Troubleshooting Chart for Controlhead CM140/340 ...........................................3-1 1.1 On/Off ............................................................................................................3-1 1.2 Microprocessor ..............................................................................................3-2 2.0 Troubleshooting Chart for Controlhead CM160/360 ............................................3-3 2.1 On/Off ............................................................................................................3-3 2.2 Microprocessor ..............................................................................................3-4 2.3 Display ...........................................................................................................3-5 2.4 Backlight ........................................................................................................3-6 iv Chapter 4 CONTROLHEAD PCB/SCHEMATICS/PARTS LISTS 1.0 Allocation of Schematics and Circuit Boards ....................................................... 4-1 2.0 Controlhead CM140/340 - PCB 8488998U01 Schematics.................................. 4-3 2.1 Controlhead PCB 8488998U01 - Parts List.................................................... 4-5 3.0 Controlhead CM160/360 - PCB 8489714U01 Schematics ................................. 4-6 3.1 Controlhead PCB 8489714U01 - Parts List ................................................... 4-8 Chapter 1 OVERVIEW 1.0 CM140/CM340Models The Controlhead contains the internal speaker, the on/off/volume knob, the microphone connector, several buttons to operate the radio, three indicator Light Emitting Diodes (LED) to inform the user about the radio status, and a single character 7-segment display for numeric information e.g. channel number. 2.0 CM160/CM360Models The Controlhead contains the internal speaker, the on/off/volume knob, the microphone connector, several buttons to operate the radio, three indicator Light Emitting Diodes (LED) to inform the user about the radio status, and an 8 character Liquid Crystal Display (LCD) for alpha - numerical information e.g. channel number or call address name. 1-2 OVERVIEW Chapter 2 THEORY OF OPERATION 1.0 Introduction This Chapter provides a detailed theory of operation for the Controlhead circuits. For details of the trouble shooting refer to the related chapter in this section. 2.0 Controlhead Model for CM140 and CM340 The controlhead contains the internal speaker, the on/off/volume knob, the microphone connector, several buttons to operate the radio and three indicator Light Emitting Diodes (LED) to inform the user about the radio status and a 7-segment display for numeric information. 7-segment display 9.3V BCD To 7-segment Shift Register Control line Boot_res / SCI DTMF Resistors Mux. Control PTT circuit DTMF Row/Column Row/Column 9.3V Keypads Keypad Backlight Boot_res (DTMFColumn)/ SCI (DTMF-Row) 2 pin speaker connector 2.1 Power Supplies The power supply to the control head is taken from the host radio’s 9.3V via connector J803-9, The 9.3V is used for the LEDs and back light, the 5V is used for the LCD driver and level shifter. The stabilized 3V is used for the other parts. 2.2 SPI Interface The host radio (master) communicates with the control head through its SPI bus. Three lines are connected to the shift register (U801):SPI clock (J803-17), SPI MOSI (J803-16) and shift register chip select (J803-15). 2-2 THEORY OF OPERATION When the host radio needs to send date to the shift register, the radio asserts the shift register chip select and the data is loaded to the shift register. For example, the host radio sends data to change display channel or change LED status. 2.3 Keypad Keys The control head keypad is a four-key design. All keys are configured as two analog lines read by µP. The voltage on the analog lines varies between 0V and 3.3 V depending on which key is pressed. If no key is pressed, the voltage at both lines is 3.3V. The key configuration can be thought of as a matrix where the two lines represent one row and one column. Each line is connected to a resistive divider powered by 3.3V. If a button is pressed, it will connect one specific resistor of each divider line to ground level and thereby reduce the voltages on the analog lines. The voltages of the lines are A/D converted inside the µP (ports PE 6 - 7) and specify the pressed button. To determine which key is pressed, the voltage of both lines must be considered. The same analog lines also support a keypad microphone. A microphone key press is processed in the same manner like a control head key press. 2.4 Status LED’s and Back Light Circuit All indicator LEDs (red, yellow, and green) are driven by current sources. To change the LED status the host radio sends a data message to the control head shift register via the SPI bus. The control head shift register determines the LED status from the received data and switches the LEDs on or off via Q5-Q7. The back light for the keypad is always on. The back light current for the keypad is drawn from the 9.3 V source and controlled by two current sources. The LED current is determined by the resistor at the emitter of the respective current source transistor. 2.5 Microphone Connector Signals The MIC_PTT line (J802-3) is grounded when the PTT button on the microphone is pressed. When released, this line is pulled to 9.3V by R805. Two transistor stages (Q802, Q801 and associated parts) are used to level shift between 9.3V and 3.3V required for the uP while keeping the same sense (active low for PTT pressed). Two of the mic socket lines (J802-2,7) have dual functions depending on the type of microphone or SCI lead connected. An electronic switch (U803) is used to switch these two lines between mic keypad operation or SCI operation. The switch (mux) is controlled by the uP through J803-20 with level shifting (and inversion) provided by transistor Q812. When MUX_CTRL (J803-20) is low the electronic switch is in the mic keypad mode. The mic socket (J802) pin 2 is connected to the keypad row line that goes to J803-13 and pin 7 is connected to the keypad column line that goes to J803-12. When MUX_CTRL (J803-20) is high the electronic switch is in the SCI mode. The mic socket (J802 pin 2) is connected to the SCI line that goes to J803-4 and pin 7 is connected to the BOOT_RES line that goes to J803-11. The HOOK line (J802-6) is used to inform the uP which type of microphone or SCI lead is connected to the microphone socket. The voltage of the HOOK line is monitored by the uP (port PE0, MIC_SENSE) through a resistor divider on the main board. When the HOOK line is grounded (on hook condition) or floating (2.8V nominal), the uP sets the mux (U803) for keypad operation to allow the use of microphones with a keypad. When the HOOK line is connected to 9.3V, the uP sets the mux for SCI operation. This mode is also used to select low cost mic operation where the gain of the microphone path is increased (on the main board) to compensate for not having a pre-amp in the low cost mic. Controlhead Model for CM140 and CM340 2-3 If the BOOT_RES (J802-7) line is connected to >5V (e.g. 9.3V) at turn-on, the uP will start in boot mode instead of normal operation. This mode is used to programme new firmware into the FLASH memory (U404 mainboard). 2.6 Speaker The controlhead contains a speaker for the receiver audio. The receiver audio signal from the differential audio output of the audio amplifier located on the radio’s controller is fed via connector J803-1, 2 to the speaker connector P801 pin 1 and pin 2. The speaker is connected to the speaker connector P801. The controlhead speaker can be disconnected if an external speaker, connected on the accessory connector, is used. 2.7 Electrostatic Transient Protection Electrostatic transient protection is provided for the sensitive components in the controlhead by diodes VR801, VR802, VR803 and VR804. The diodes limit any transient voltages to tolerable levels. The associated capacitors provide Radio Frequency Interference (RFI) protection. 2-4 3.0 THEORY OF OPERATION Controlhead Model for CM160 and CM360 The controlhead contains the internal speaker, the on/off/volume knob, the microphone connector, several buttons to operate the radio, three indicator Light Emitting Diodes (LED) to inform the user about the radio status, and an 8 character Liquid Crystal Display (LCD) for alpha - numerical information e.g. channel number or call address name. 9.3V LCD LED Backlight LED Indicators LCD Driver Level Shifter 9.3V Backlight Control Shift Register Control line Boot_Res / SCI Keypad Resistors Mux. Control PTT circuit DTMF Row/Column 8 pin JACK connector Row/Column Keypads Boot_Res (DTMFColumn)/ SCI (DTMF-Row) 2-pin speaker connector 3.1 Power Supplies The power supply to the control head is taken from the host radio’s 9.3V via connector J103-9, The 9.3V is used for the LEDs and back light, the 5V is used for the LCD driver (U3) and level shifter (U4). The stabilized 3V is used for the other parts. 3.2 SPI Interface The host radio (master) communicates with the control head through its SPI bus. Three lines are connected to the shift register (U8):SPI clock (J103-17), SPI MOSI (J103-16), shift register chip select (J103-15) and LCD driver chip select (J103-18). When the host radio needs to send date to the shift register, the radio asserts the shift register chip select and the data is loaded to the shift register. For example, the host radio sends data to change display channel or change LED status. Controlhead Model for CM160 and CM360 3.3 2-5 Keypad Keys The control head keypad is a four-key design. All keys are configured as two analog lines read by µP. The voltage on the analog lines varies between 0V and 3.3 V depending on which key is pressed. If no key is pressed, the voltage at both lines is 3.3V. The key configuration can be thought of as a matrix where the two lines represent one row and one column. Each line is connected to a resistive divider powered by 3.3V. If a button is pressed, it will connect one specific resistor of each divider line to ground level and thereby reduce the voltages on the analog lines. The voltages of the lines are A/D converted inside the µP (ports PE 6 - 7) and specify the pressed button. To determine which key is pressed, the voltage of both lines must be considered. The same analog lines also support a keypad microphone. A microphone key press is processed in the same manner like a control head key press. 3.4 LCD Driver The LCD (36 x 4 segemnts) is controlled by U3. It has an on onboard clock controlled by R28 (typically 20kHz measured on pin 2). U3 is operated from the 5V supply and is controlled over the SPI bus (SPI_CLK J103-17, SPI_MOSI J103-16, LCD chip select J103-18). Chip select is active low. U2 is used to provide level shifting between the 3.3V logic from the uP and the 5V required by U3. 3.5 Status LED’s and Back Light Circuit All indicator LEDs (red, yellow, and green) are driven by current sources. To change the LED status the host radio sends a data message to the control head shift register via the SPI bus. The control head shift register determines the LED status from the received data and switches the LEDs on or off via Q8-Q10. Backlighting for the LCD and keys is provided by a matrix of 21 LEDs arranged in 7 columns of 3 rows. The LEDs are driven from a constant current circuit (Q12, U1 and associated parts). There are 4 levels of baclight: off, low, medium and high, which are controlled by two outputs (pins 15, 1) from the shift register (U8). The current is controlled by transistor Q12. The op amp U1 monitors the current by measuring the voltage drop across R26, R27 and adjusting the bias of Q12 to achieve the required level as set by the combined shift register o/ps. When in the off state, Q11 is also turned on to clamp the base of Q12 so as to force it off. This ensures that the LEDs are fully off. Q11 is controlled by pin 3 of the shift register U8. 3.6 Microphone Connector Signals The MIC_PTT line (J102-3) is grounded when the PTT button on the microphone is pressed. When released, this line is pulled to 9.3V by R33. Two transistor stages (Q14, Q13 and associated parts) are used to level shift between 9.3V and 3.3V required for the uP while keeping the same sense (active low for PTT pressed). Two of the mic socket lines (J102-2, 7) have dual functions depending on which type of microphone or SCI lead that is connected. An electronic switch (U41) is used to switch these two lines between mic keypad operation or SCI operation. The switch (mux) is controlled by the uP through J103-20 with level shifting (and inversion) provided by transistor Q41. When MUX_CTRL (103-20) is low the electronic switch is in the mic keypad mode. The mic socket (J102) pin 2 is connected to the keypad row line that goes to J103-13 and pin 7 is connected to the keypad column line that goes to 103-12. When MUX_CTRL (103-20) is high the electronic switch is in the SCI mode. The mic socket (J102 pin 2) is connected to the SCI line that goes to J103-4 and pin 7 is connected to the BOOT_RES line that goes to J103-11. 2-6 THEORY OF OPERATION The HOOK line (J102-6) is used to inform the uP which type of microphone or SCI lead is connected to the microphone socket. The voltage of the HOOK line is monitored by the uP (port PE0, MIC_SENSE) through a resistor divider on the main board. When the HOOK line is grounded (on hook condition) or floating (2.8V nominal), the uP sets the mux (U8) for keypad operation to allow the use of microphones with a keypad. When the HOOK line is connected to 9.3V, the uP sets the mux for SCI operation. This mode is also used to select low cost mic operation where the gain of the microphone path is increased (on the main board) to compensate for not having a pre-amp in the low cost mic. If the BOOT_RES (J102-7) line is connected to >5V (e.g. 9.3V) at turn-on then the uP will start in boot mode instead of normal operation. This mode is used to programme new firmware into the FLASH memory (U404 mainboard). 3.7 Speaker The controlhead contains a speaker for the receiver audio. The receiver audio signal from the differential audio output of the audio amplifier located on the radio’s controller is fed via connector J103-1, 2 to the speaker connector P101 pin 1 and pin 2. The speaker is connected to the speaker connector P101. The controlhead speaker can be disconnected if an external speaker, connected on the accessory connector, is used. 3.8 Electrostatic Transient Protection Electrostatic transient protection is provided for the sensitive components in the controlhead by diodes VR1 - VR4. The diodes limit any transient voltages to tolerable levels. The associated capacitors provide Radio Frequency Interference (RFI) protection. Chapter 3 TROUBLESHOOTING CHARTS 1.0 1.1 Controlhead CM140/CM340 Troubleshooting Chart Control Head Failure Control Head Check Back light OK ? Check 9.3V on R808, R809 No YES Power-up Alert Tone OK ? No Check Speaker Connection No Check D801, Q806, U801 YES Power-up Red LED Flash ? YES Channel Display OK? No Check DS801, U801, U802 YES Up/Down P1 and P2 Alert Tone Buttons OK? No Check R845, R846 R810, R811 YES EXT PTT OK ? No YES Communication Ok Control Head is OK Check Q801, Q802 No Check Q803, Q812 3-2 1.2 TROUBLESHOOTING CHARTS Button/Tones Select Error (Page 1 of 2) Button/Tones Check Check Voltage Levels on TP401 (Keypad Col) and TP402 (Keypad Row) (see table on next page) Right Voltage Up Key No Check R846, R811 on Control Head ? YES Right Voltage No on Down Key ? Check R845, R810 on Control Head YES Right Voltage on P1/P2 Keys ? No Check R813, R814 on Control Head YES Connect DTMF Mic to TELCO Connector Is there 0.75 Vdc on MIC_SENSE R429, on radio A No Check Control Head connectivity continuity and R429, R430, D401 (main board) Controlhead CM140/CM340 Troubleshooting Chart Button/Tones Select Error (Page 2 of 2) A Right Voltage on DTMF keys ? Does Q812 on Control Head operates well ? No YES Key_Col Voltage (TP401) No Replace Q812 YES Replace U803 on Control Head Button/Tones Keys Okay Key_Row Voltage TP402 1.3 3-3 Key_Column Voltage TP401 0.008 V 0.675 V 1.346 V 1.997 V 2.650 V 0.008 V Up 0.675 V 1 2 3 1.346 V 4 5 6 7 1.997 V 8 9 0 * 2.650 V # C B A Left Key P1 Right Key P2 3.300 V 3.300 V Down Idle 3-4 2.0 2.1 TROUBLESHOOTING CHARTS Controlhead CM160/CM360 Troubleshooting Chart Control Head Failure Control Head Check Back light OK ? Check 9.3V on Q12, U1 and associated parts and U8 No YES Power-up Alert Tone OK ? No Check Speaker Connection No Check Q8-Q10, U8 and 9.3V YES Indicator LED’S OK ? YES Display OK? No Check LCD connections, U3 for 5V, Osc. pins 1 & 2 activity SCI thru via U4 YES Up/Down P1 and P2 Alert Tone Buttons OK? No Check keypad resistors YES EXT PTT OK ? No YES Communication Ok Control Head is OK Check Q13, Q802 No Check Q803, Q14 and associated parts Controlhead CM160/CM360 Troubleshooting Chart 2.2 3-5 Button/Tones Select Error (Page 1 of 2) Button/Tones Check Check Voltage Levels on TP401 (Keypad Col) and TP402 (Keypad Row) (see table on next page) Right Voltage Up Key? No Check R13, R45 on Control Head No Check R12, R49 on Control Head No Check R31, R29 R51, R11 on Control Head YES Right Voltage on Down Key? YES Right Voltage on P1-P4 Keys ? YES Connect DTMF Mic to TELCO Connector Is there 0.75 Vdc on MIC_SENSE R429, on radio A No Check Control Head connectivity continuity and R429, R430, D401 (Main Board) 3-6 Button/Tones Select Error (Page 2 of 2) A Right Voltage on DTMF keys ? Does Q41 on Control Head operates well ? No YES Key_Col Voltage (TP401) No Replace Q41 YES Replace U8 on Control Head Button/Tones Keys Okay Key_Row Voltage TP402 2.3 TROUBLESHOOTING CHARTS Key_Column Voltage TP401 0.008 V 0.675 V 1.346 V 1.997 V 2.650 V 0.008 V Up 0.675 V 1 2 3 1.346 V 4 5 6 7 1.997 V 8 9 0 * 2.650 V # C B A Left Key P1 Right Key P2 P3 P4 3.300 V 3.300 V Down Idle Chapter 4 CONTROLHEAD PCB / SCHEMATICS / PARTS LISTS 1.0 Allocation of Schematics and Circuit Boards Table 4-1 Controlhead Diagrams and Parts Lists PCB : Controlhead CM140/CM340 8488998U01 Main Board Top Side 8488998U01 Main Board Bottom Side Page 4-3 Page 4-3 SCHEMATICS Sheet 1 of 1 Page 4-4 Parts List 8488998U01 Page 4-5 Table 4-2 Controlhead Diagrams and Parts Lists PCB : Controlhead CM160/CM360 8489714U01 Main Board Top Side 8489714U01 Main Board Bottom Side Page 4-6 Page 4-6 SCHEMATICS Sheet 1 of 1 Page 4-7 Parts List 8489714U01 Page 4-8 4-2 CONTROLHEAD PCB / SCHEMATICS / PARTS LISTS THIS PAGE INTENTIONALLY LEFT BLANK Controlhead CM140/CM340 - PCB 8488998U01 / Schematics Controlhead CM140/CM340 - PCB 8488998U01 / Schematics D802 D801 D803 J804 DS801 D806 SH1 J805 J802 S802 D805 D804 S801 Top Side SHOWN FROM SIDE 1 8488998u01_p3 C814 C802 C801 C813 C803 C805 C804 C811 C806 C812 C809 C807 C810 C808 R808 R818 R809 R819 R820 Bottom Side SHOWN FROM SIDE 2 Q802 R807 R806 Q801 C822 C821 C820 C819 VR802 VR804 R833 M804 C818 C816 C817 M802 C815 1 R840 R801 R804 R834 VR803 C823 R805 R802 C833 C836 R841 R810 R844 R811 R839 1 R848 R842 Q803 R829 R816 R847 1 R813 R842 C832 Q812 U801 R846 C834 R830 R850 P801 C825 C824 R826 R827 R821 R822 R823 R824 R825 J803 C826 R803 C827 R845 R843 R832 Q811 R849 1 Q806 R831 1 Q805 1 M801 1 1 Q804 M803 2.0 4-3 Controlhead CM140/CM340 PCB 8488998U01 4-4 Controlhead CM140/CM340 - PCB 8488998U01 / Schematics D3_3V C824 R842 R847 10.K 10.K 1 C825 220.p M801 100n THESE ARE THE 1 BI M802 ESD PROTECTION D3_3V 1 M803 DNP CONTACTS (SPRINGS) 1 M804 9_3V C826 DS801 C827 R829 R843 100n 10.K 10.K DNP 9_3V R821 33. R822 33. 220.p D3_3V 16 HDSP-513G R820 3.9K 680. 680. ANODE_D A2 LE B2 BI 4 ANODE_G ANODE_DP 33. R826 33. R827 33. J803-17 C2 15 Q0 1 2 3 4 8 5 J803-16 CLK_S Q2 CLK_L Q3 EN_OE Q4 RESET Q6 7 J803-15 Q1 Q5 6 11 J803-12 12 J803-13 13 J803-2 10 J803-1 U801 MC74HC595A Q7 9 SEROUT SERIN R850 J803-3 0. J803-4 10K J803-6 J803-11 R830 470. J803-18 BI Q803 10K 100n D3_3V J803-10 C834 C832 4 3 2 1 SHIELD R802 R844 C801 C803 3.3K 220.p OE DNP C805 220.p C809 220.p C811 220.p C813 220.p SPI_MOSI 12 KEY_COL 13 KEY_ROW 2 SPKR+ SPKR- 3 RX. AUDIO 4 SCI 5 MIC. PTT MIC. AUDIO 8 HOOK 11 BOOT_RES 20 DISP_CS 18 COM/DATA_SEL 7 J803-21 C807 220.p SH_R_CS 16 G1 J803-22 G2 220.p 10K 10.K Place under the 7-segment DNP SPI_CLK 15 10 J803-7 DNP 22.n 47K 10K Q805 J803-20 DISPL_CS SH1 DIS_RES 17 6 J803-8 8 Q804 19 1 J803-5 CH_PTT DNP 14 GND 9_3V 47K 14 9 J803-19 OE 3 LT U802 D2 MC14511BFEL 7 A1 E 1 15 B1 F 2 14 G C1 6 D1 10 GREEN LED YELLOW LED RED LED 33. R825 ANODE_C D803 R824 12 9 ANODE_F HSMG-C670 HSMY-C670 HSMH-C670 D802 33. 11 COMM_CATH_2 COMM_CATH_1 D801 R823 VSS R819 J803-9 16 ANODE_A R818 MAIN BOARD CONNECTOR J803-14 5 VCC 13 VDD ANODE_B ANODE_E Q811 47K 10K 47K DISPL_CS Q812 C802 C815 R801 47K 10u 9_3V C804 220.p C806 220.p 0. C808 220.p C810 220.p C812 220.p C814 220.p 220.p 10K Q806 47K DNP 100n 9_3V 220.p 0. C836 2 1 5 VCC Y0 Y Y1 B Z0 Z Z1 C R849 8 Change to 1% A GND 3 X X1 R841 6 DNP 10.K 14 R833 11 0. 15 9_3V D3_3V 9_3V TELCO_PTT D3_3V 10 DNP 4 DNP 9 VEE 13 EN X0 R848 R846 R831 10.K 51.K 20.K DNP R832 20.K J802-8 8 9.3 V J802-7 7 BOOT_RES J802-6 6 HOOK J802-4 4 MIC. AUDIO J802-3 3 MIC. PTT J802-2 2 SCI J802-1 1 RX. AUDIO J802-5 5 R845 51.K C816 7 12 16 U803 MC14053B MICROPHONE CONNECTOR R834 9_3V C833 C820 C818 C822 13K VR801 VR803 20.0 20.0 220.p 220.p 220.p 220.p ROW Change to 1% Change to 1% R813 R816 22K 13K COL DNP KEYPAD BACKLIGHT R811 R810 0. 0. 9_3V C819 C817 9_3V VR802 VR804 20.0 20. C821 220.p 220.p 220.p SPEAKER CONNECTOR DNP 3 5 C1 C2 C3 C4 C5 C6 2 1 4 3 6 5 C1 C2 C3 C4 C5 C6 4 6 CONTACT 1 PIN1 PIN2 DOWN F2 F1 680. R839 R840 22.K 22.K D3_3V 9_3V R803 R805 R804 47.K Q801 47.K 10.K CONTACT 2 1 PIN1 PIN2 UP 2 D805 D806 CH_PTT 10K R806 Q802 47.K 47K TELCO_PTT R807 C823 1n Controlhead CM140/CM340 Schematic 10.K SPKRSPKR+ 73B02964C39-O D804 J804 J805 2 R809 300. HSMG-C670 1 R808 DNP HSMG-C670 S801 TOUCH_SW_MARLIN P801-2 2 HSMG-C670 S802 P801-1 1 ROW Change to 1% Change to 1% TOUCH_SW_MARLIN COL Controlhead CM140/CM340 - PCB 8488998U01 / Schematics 2.1 Controlhead PCB 8488998U01 Parts List Circuit Ref Motorola Part No Description 4-5 Circuit Ref Motorola Part No Description Circuit Ref Motorola Part No Description J803 0989241U02 FLEX 20-PIN 1mmTOP NON R830 0662057A41 CHIP RES 470 OHMS 5% M801 7588823L03 PAD GROUNFD LCD R841 0662057A73 CHIP RES 10K OHMS 5% M802 7588823L03 PAD GROUNFD LCD R842 0662057A73 CHIP RES 10K OHMS 5% C802 2113740F59 CAP CHIP REEL CL13 M803 7588823L03 PAD GROUNFD LCD R843 0662057A73 CHIP RES 10K OHMS 5% C804 2113740F59 CAP CHIP REEL CL13 M804 7588823L03 PAD GROUNFD LCD R844 0662057A73 CHIP RES 10K OHMS 5% C805 2113740F39 CAP CHIP REEL CL1+/-30 33 P801 2809926G01 CONN 1.25MM 2PIN SURMT R845 0662057A90 CHIP RES 51K OHMS 5% C806 2113740F39 CAP CHIP REEL CL1+/-30 33 Q801 4809940E02 TSTR NPN DIG DTC114YE R846 0662057A90 CHIP RES 51K OHMS 5% C808 2113740F59 CAP CHIP REEL CL13 Q802 4813824A10 TSTR NPN 40V .2A GEN P R849 0662057D03 CHIP RES 13K OHMS 5% C809 2113740F39 CAP CHIP REEL CL1+/-30 33 Q803 4809940E02 TSTR NPN DIG DTC114YE C810 2113740F39 CAP CHIP REEL CL1+/-30 33 Q804 4809940E02 TSTR NPN DIG DTC114YE C811 2113740F59 CAP CHIP REEL CL13 Q805 4809940E02 TSTR NPN DIG DTC114YE C812 2113740F39 CAP CHIP REEL CL1+/-30 33 Q806 4809940E02 TSTR NPN DIG DTC114YE C813 2113740F59 CAP CHIP REEL CL13 Q811 4809940E02 TSTR NPN DIG DTC114YE C814 2113740F59 CAP CHIP REEL CL13 Q812 4809940E02 TSTR NPN DIG DTC114YE C816 2113740F39 CAP CHIP REEL CL1+/-30 33 R801 0662057A01 CHIP RES 10 OHMS 5% C817 2113740F39 CAP CHIP REEL CL1+/-30 33 R802 0662057A61 CHIP RES 330 OHMS 5% C818 2113740F39 CAP CHIP REEL CL1+/-30 33 R803 0662057A89 CHIP RES 47K OHMS 5% C819 2113740F39 CAP CHIP REEL CL1+/-30 33 R804 0662057A89 CHIP RES 47K OHMS 5% C820 2113740F39 CAP CHIP REEL CL1+/-30 33 R805 0662057A73 CHIP RES 10K OHMS 5% C821 2113740F29 CAP CHIP REEL CL1+/-30 12 R806 0662057A89 CHIP RES 47K OHMS 5% C822 2113740F39 CAP CHIP REEL CL1+/-30 33 R807 0662057A73 CHIP RES 10K OHMS 5% C823 2113743K15 CER CHIP CAP .100uF R808 0662057A36 CHIP RES 300 OHMS 5% C824 2113740F59 CAP CHIP REEL CL13 R809 0662057A45 CHIP RES 680 OHMS 5% C825 2113743K15 CER CHIP CAP .100uF R810 0662057B47 CHIP RES 0 OHMS +0.5 C826 2113740F59 CAP CHIP REEL CL13 R811 0662057B47 CHIP RES 0 OHMS +0.5 C827 2113743K15 CER CHIP CAP .100uF R813 0662057D08 CHIP RES 22K OHMS 5% C832 2113743K15 CER CHIP CAP .100uF R816 0662057D03 CHIP RES 13K OHMS 5% C833 2113743K15 CER CHIP CAP .100uF R818 0662057A63 CHIP RES 3900 OHMS 5% C834 2113743E07 CER CHIP CAP .022uF R819 0662057A45 CHIP RES 680 OHMS 5% C836 2113740F59 CAP CHIP REEL CL13 R820 0662057A45 CHIP RES 680 OHMS 5% D801 4805729G74 LED SMT RED HP R821 0662057A13 CHIP RES 33 OHMS 5% D802 4805729G73 LED SMT YEL HP R822 0662057A13 CHIP RES 33 OHMS 5% D803 4805729G75 LED SMT GREEN HP R823 0662057A13 CHIP RES 33 OHMS 5% D804 4805729G75 LED SMT GREEN HP R824 0662057A13 CHIP RES 33 OHMS 5% D805 4805729G75 LED SMT GREEN HP R825 0662057A13 CHIP RES 33 OHMS 5% D806 4805729G75 LED SMT GREEN HP R826 0662057A13 CHIP RES 33 OHMS 5% DS801 5180353L02 7-SEGMENT DISPLAY R827 0662057A13 CHIP RES 33 OHMS 5% J802 0908353Y02 MODULAR 8-PIN STR R829 0662057A73 CHIP RES 10K OHMS 5% C33 R22 C18 R21 R17 R16 R54 R31 Q14 VR2 R3 Q41 1 VR1 VR3 16 C34 R38 C5 R33 R43 D26 D9 D20 S2 1 1 1 1 D4 S1 C3 12 M1 R48 R12 4 5 S4 C29 J103 R34 R50 R25 C24 R13 R46 R45 R44 R18 C17 U1 R19 R27 R26 S3 C42 C40 R36 R49 C41 C45 C8 C44 C46 C48 C47 C50 C27 C4 C49 C38 C51 C52 C53 C55 C54 R35 1 1 8 3 D12 D13 D23 D25 D22 D11 D16 D15 D14 D17 D21 D8 D5 D27 D3 D24 DS1 R42 C2 R40 R14 C7 C15 Q13 R41 C56 M2 16 1 24 C14 C58 R23 U8 R30 9 R39 8 C32 Q10 C30 Q9 R28 7 48 8 U3 Q8 R9 37 U2 C16 R8 R7 R6 2 R15 C20 M4 R20 R24 C11 C26 Q11 2 D18 R29 M3 1 8 D19 R51 14 4 P101 C36 C25 R10 U18 4 Q12 6 7 5 3 4 D2 C39 C21 C22 1 5 C35 R11 C23 8 C19 9 2 3.0 1 4-6 Controlhead CM160/CM360 - PCB 8489714U01 / Schematics Controlhead CM160/CM360 - PCB 8489714U01 / Schematics 1 S6 1 D10 Top Side S5 J102 R37 C43 C6 Bottom Side VR4 C1 U41 9 8 Controlhead CM160/CM360 PCB 8489714U01 Controlhead CM160/CM360 - PCB 8489714U01 / Schematics 4-7 D3_3V COM3 4 COM2 3 COM1 2 COM0 1 9_3V R37 47K SEG31 SEG30 SEG29 SEG28 SEG27 SEG26 SEG25 SEG24 SEG23 SEG22 SEG21 SEG20 SEG19 SEG18 SEG17 SEG16 SEG15 SEG14 SEG13 SEG12 SEG11 SEG10 SEG9 SEG8 SEG7 SEG6 SEG5 SEG4 SEG3 SEG2 SEG1 SEG0 DS1 LCD_36PIN DNF R36 36 35 34 33 32 31 30 29 28 27 26 25 24 23 22 21 20 19 18 17 16 15 14 13 12 11 10 9 8 7 6 5 5V_CH Q14 48 47 46 45 44 43 42 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 22 21 20 19 18 17 CK 0 C30 100pF DNF R30 10K DNF D3_3V U2-1 MC74HCT04A 2 13 R23 680 9_3V 9_3V 9_3V SI Q9 47K R54 ROW 9_3V Q8 R44 20K DNF HSMG-C670 D24 HSMG-C670 D22 R51 43K VDD C48 220pF DNF C46 220pF DNF C44 220pF DNF EN 6 C52 470pF R35 3.3K R43 0 DNF 15 ZB 10 SB C47 220pF DNF C45 220pF DNF 9_3V R42 0 DNF 4 ZC 9 SC C49 470pF MICROPHONE CONNECTOR R13 51K S6 TOUCH_SW DNF S1 TOUCH_SW DNF S2 TOUCH_SW DNF 1 C1 3 C3 5 C5 R16 2 C2 4 C4 6 C6 1 C1 3 C3 5 C5 1 2 C2 4 C4 6 C6 2 R46 22K DNF 9_3V UP C2 470pF C27 1000pF DNF 8 J102-8 7 J102-7 BOOT_RES 6 J102-6 HOOK 4 J102-4 MIC. AUDIO 3 J102-3 MIC. PTT 2 J102-2 SCI 1 J102-1 RX. AUDIO 5 J102-5 1 P101-1 SPKR- 2 P101-2 SPKR+ 9.3 V F4 C5 470pF C3 470pF C6 1000pF DNF D3_3V VR4 20V 27K C42 1000pF DNF VR2 20V C29 1000pF DNF C34 1000pF DNF + F3 R29 R31 22K 13K R48 20K DNF R12 51K VR1 20V VR3 20V R49 0 C17 1000pF DNF S5 TOUCH_SW DNF R18 1K S3 TOUCH_SW DNF R19 10K 1 C1 3 C3 5 C5 2 C2 4 C4 6 C6 1 C1 3 C3 5 C5 2 C2 4 C4 6 C6 2 1 DOWN - F2 Controlhead CM160/CM360 Schematic F1 5V_CH R50 22K DNF C4 1000pF DNF U1-2 LM2904 7 8 6 5 4 14 R20 10K DNF S4 TOUCH_SW DNF R27 10 Y1C C51 220pF DNF DIS_RES SPI_CLK SH_R_CS SPI_MOSI KEY_COL KEY_ROW SPKR+ SPKRRX. AUDIO SCI MIC. PTT MIC. AUDIO HOOK BOOT_RES DISP_CS COM/DATA_SEL 2 47K R26 10 C53 220pF DNF J103-14 J103-9 J103-19 J103-17 J103-15 J103-16 J103-12 J103-13 J103-2 J103-1 J103-3 J103-4 J103-5 J103-6 J103-8 J103-11 J103-20 J103-18 J103-10 J103-7 J103-21 J103-22 0.1uF C18 0.1uF VCC GND 7 Q11 CH_PTT R3 10 R45 0 C39 1000pF DNF R11 130K 3 10K DNF 14 9 19 17 15 16 12 13 2 1 3 4 5 6 8 11 20 18 10 7 G1 G2 TELCO_PTT 4 2.2K Q12 C1 10uF 14 ZA 11 SA 1 Y1B 5 Y0C 3 D3_3V 10K HSMG-C670 D25 HSMG-C670 D23 HSMG-C670 D21 HSMG-C670 D20 HSMG-C670 D9 HSMG-C670 D4 HSMG-C670 D8 HSMG-C670 D5 HSMG-C670 D27 R24 8 YOA 13 Y1A 2 Y0B COL 13K U1-1 LM2904 1 16 U41 HEF4053B 13K R17 C11 0.1uF R41 10K C56 9_3V 47K 12 HSMG-C670 D13 HSMG-C670 D12 HSMG-C670 D11 HSMG-C670 D16 HSMG-C670 D15 HSMG-C670 D14 HSMG-C670 D17 HSMG-C670 D3 HSMG-C670 D2 HSMG-C670 D26 C40 1000pF DNF C26 1000pF C14 0.1uF DNF MUX_CTL CS 47K C41 1000pF DNF 9_3V Q41 10K CS 9_3V 11 12 13 10 Q10 10K MAIN BOARD CONNECTOR CK 10K MUX_CTL 1 3 5 9_3V 9_3V C38 1000pF DNF R40 10K CK 9_3V C54 470pF Q7 14 SEROUT SERIN VSS 8 VEE 7 C25 1000pF DNF U2-2 MC74HCT04A 4 11 GND 4 C20 2.2uF DNF R22 680 R21 3.9K 47K 9_3V Q0 CLK_S Q1 Q2 CLK_L EN_OE Q3 Q4 RESET U8 Q5 MC74HC595A Q6 8 C32 100pF DNF 9_3V SI R10 0 DNF C55 220pF DNF C58 .022uF GND 9_3V D18 HSMY-C670 C33 100pF DNF D19 HSMH-C670 R9 1 5 2 6 15 1 2 3 4 5 6 7 9 R39 10K 9_3V U2-3 MC74HCT04A 9 6 8 INPUT OUTPUT 7 FEEDBACK ERROR 3 SHUTDOWN SENSE 5V_TAP 680K U2-6 MC74HCT04A 12 U18 LP2951C DNF R8 10K DNF U2-5 MC74HCT04A 10 R15 10K DNF U2-4 MC74HCT04A 8 C22 0.1uF C50 470pF R14 10K 5V_CH R28 C21 4.7uF DNF C15 0.1uF 16 12 13 14 15 6 8 COM0 COM1 COM2 COM3 VSS C7 1000pF R34 10K D10 HSMG-C670 SI 9 11 CS OSC1 1 OSC2 2 R7 10K DNF C_D U3 S1D15100 C43 0.1uF VCC VDD 3 V1 4 V2 5 V3 10 7 VREG R6 10K DNF 16 C24 1000pF C16 0.1uF SEG31 SEG30 SEG29 SEG28 SEG27 SEG26 SEG25 SEG24 SEG23 SEG22 SEG21 SEG20 SEG19 SEG18 SEG17 SEG16 SEG15 SEG14 SEG13 SEG12 SEG11 SEG10 SEG9 SEG8 SEG7 SEG6 SEG5 SEG4 SEG3 SEG2 SEG1 SEG0 0 C23 1000pF TELCO_PTT 47K C8 1000pF C19 2.2uF D3_3V D3_3V R25 9_3V 9_3V 5V_IN 10K Q13 47K 5V_IN R33 10K R38 47K CH_PTT U2-7 PWR_GND C35 1000pF DNF C36 1000pF DNF SPEAKER CONNECTOR ESD CONTACTS M1 M2 M3 M4 Controlhead CM160/CM360 - PCB 8489714U01 / Schematics 3.1 Controlhead PCB 8489714U01 Parts List Circuit Ref Motorola Part No Description 4-8 Circuit Ref Motorola Part No Description Circuit Ref Motorola Part No Description Circuit Ref Motorola Part No Description C44 NOTPLACED CAP, 220pF J102 0908353Y02 CONN_J R29 0662057A81 RES, 22K C45 NOTPLACED CAP, 220pF J103 0989241U02 CONN_J R30 NOTPLACED RES, 10K C46 NOTPLACED CAP, 220pF M1 7588823L03 CONTACT R31 0662057A76 RES, 13K NOTPLACED CAP, 220pF M2 7588823L03 CONTACT R33 0662057A73 RES, 10K C1 NOTPLACED CAP, 10uF C47 C2 2113740F67 CAP, 470pF C48 NOTPLACED CAP, 220pF M3 7588823L03 CONTACT R34 0662057A73 RES, 10K 2113740F67 CAP, 470pF M4 7588823L03 CONTACT R35 0662057A61 RES, 3.3K C3 2113740F67 CAP, 470pF C49 C4 2113740F12 CAP CHIP REEL CL1 +/-30 12 C50 2113740F67 CAP, 470pF P101 2809926G01 CONN_P R36 0662057A89 RES, 47K C5 2113740F67 CAP, 470pF C51 2113740F12 CAP CHIP REEL CL1 +/-30 12 Q8 4809940E02 DTC114YE R37 0662057A89 RES, 47K C6 2113740F12 CAP CHIP REEL CL1 +/-30 12 C52 2113740F67 CAP, 470pF Q9 4809940E02 DTC114YE R38 0662057A89 RES, 47K C7 2113741F25 CAP, 1000pF C53 2113740F12 CAP CHIP REEL CL1 +/-30 12 Q10 4809940E02 DTC114YE R39 0662057A73 RES, 10K C8 2113741F25 CAP, 1000pF C54 2113740F67 CAP, 470pF Q11 4809940E02 DTC114YE R40 0662057A73 RES, 10K C11 2113743K15 CAP, 0.1uF C55 NOTPLACED CAP, 220pF Q12 4813824B01 PZT2222A R41 0662057A73 RES, 10K C14 NOTPLACED CAP, 0.1uF C56 2113743K15 CAP, 0.1uF Q13 4809940E02 DTC114YE R42 NOTPLACED RES, 0 C15 2113743K15 CAP, 0.1uF C58 2113743E07 CAP, .022uF Q14 4813824A10 MMBT3904 R43 NOTPLACED RES, 0 C16 2113743K15 CAP, 0.1uF D2 4805729G75 HSMG-C670 Q41 4809940E02 DTC114YE R44 NOTPLACED RES, 20K C17 NOTPLACED CAP, 1000pF D3 4805729G75 HSMG-C670 R3 0662057A01 RES, 10 R45 0662057B47 C18 2113743K15 CAP, 0.1uF D4 4805729G75 HSMG-C670 R6 NOTPLACED RES, 10K R46 NOTPLACED RES, 22K C19 2113743F18 CAP, 2.2uF D5 4805729G75 HSMG-C670 R7 NOTPLACED RES, 10K R48 NOTPLACED RES, 20K C20 NOTPLACED CAP, 2.2uF D8 4805729G75 HSMG-C670 R8 NOTPLACED RES, 10K R49 0662057B47 C21 NOTPLACED CAPP, 4.7uF D9 4805729G75 HSMG-C670 R9 0662057B47 RES, 0 R50 NOTPLACED RES, 22K C22 2113743K15 CAP, 0.1uF D10 4805729G75 HSMG-C670 R10 NOTPLACED RES, 0 R51 0662057A88 RES, 43K 4805729G75 HSMG-C670 R11 0662057B01 RES, 130K R54 0662057A76 RES, 13K RES, 0 RES, 0 C23 2113741F25 CAP, 1000pF D11 C24 2113741F25 CAP, 1000pF D12 4805729G75 HSMG-C670 R12 0662057A90 RES, 51K S1 NOTPLACED TOUCH_SW C25 NOTPLACED CAP, 1000pF D13 4805729G75 HSMG-C670 R13 0662057A90 RES, 51K S2 NOTPLACED TOUCH_SW C26 2113741F25 CAP, 1000pF D14 4805729G75 HSMG-C670 R14 0662057A73 RES, 10K S3 NOTPLACED TOUCH_SW C27 2113740F12 CAP CHIP REEL CL1 +/-30 12 D15 4805729G75 HSMG-C670 R15 NOTPLACED RES, 10K S4 NOTPLACED TOUCH_SW C29 2113740F12 CAP CHIP REEL CL1 +/-30 12 D16 4805729G75 HSMG-C670 R16 0662057A83 RES, 27K S5 NOTPLACED TOUCH_SW C30 NOTPLACED CAP, 100pF D17 4805729G75 HSMG-C670 R17 0662057A76 RES, 13K S6 NOTPLACED TOUCH_SW C32 NOTPLACED CAP, 100pF D18 4805729G73 HSMY-C670 R18 0662057A49 RES, 1K U1 5113818A01 LM2904 C33 NOTPLACED CAP, 100pF D19 4805729G74 HSMH-C670 R19 0662057A73 RES, 10K U2 5113805A05 MC74HCT04A C34 2113740F12 D20 4805729G75 HSMG-C670 R20 NOTPLACED RES, 10K U3 5102109U01 S1D15100 C35 NOTPLACED CAP, 1000pF D21 4805729G75 HSMG-C670 R21 0662057A63 RES, 3.9K U8 5113805A75 MC74HC595A C36 NOTPLACED CAP, 1000pF D22 4805729G75 HSMG-C670 R22 0662057A45 RES, 680 U18 NOTPLACED LP2951C C38 NOTPLACED CAP, 1000pF D23 4805729G75 HSMG-C670 R23 0662057A45 RES, 680 U41 5184704M60 HEF4053B C39 NOTPLACED CAP, 1000pF D24 4805729G75 HSMG-C670 R24 0662057A57 RES, 2.2K VR1 4813830A75 MMBZ20VAL C40 NOTPLACED CAP, 1000pF D25 4805729G75 HSMG-C670 R25 0662057B47 RES, 0 VR2 4813830A75 MMBZ20VAL C41 NOTPLACED CAP, 1000pF D26 4805729G75 HSMG-C670 R26 0662057A01 RES, 10 VR3 4813830A75 MMBZ20VAL C42 2113740F12 CAP CHIP REEL CL1 +/-30 12 D27 4805729G75 HSMG-C670 R27 0662057A01 RES, 10 VR4 4813830A75 MMBZ20VAL C43 2113743K15 CAP, 0.1uF DS1 NOTPLACED LCD_36PIN R28 0662057B18 RES, 680K CAP CHIP REEL CL1 +/-30 12 Commercial Series CM Radios UHF2 (438-470MHz) Service Information Issue: December 2003 ii Computer Software Copyrights The Motorola products described in this manual may include copyrighted Motorola computer programs stored in semiconductor memories or other media. Laws in the United States and other countries preserve for Motorola certain exclusive rights for copyrighted computer programs, including the exclusive right to copy or reproduce in any form, the copyrighted computer program. Accordingly, any copyrighted Motorola computer programs contained in the Motorola products described in this manual may not be copied or reproduced in any manner without the express written permission of Motorola. Furthermore, the purchase of Motorola products shall not be deemed to grant, either directly or by implication, estoppel or otherwise, any license under the copyrights, patents or patent applications of Motorola, except for the normal non-exclusive royaltyfree license to use that arises by operation of law in the sale of a product. iii Table of Contents Chapter 1 MODEL CHART AND TECHNICAL SPECIFICATIONS 1.0 CM140/CM340/CM160/CM360 Model Chart .......................................................1-1 2.0 Technical Specifications ......................................................................................1-2 Chapter 2 THEORY OF OPERATION 1.0 Introduction ..........................................................................................................2-1 2.0 UHF (438-470MHz) Receiver .............................................................................2-1 2.1 Receiver Front-End .......................................................................................2-1 2.2 Receiver Back-End.........................................................................................2-2 3.0 UHF (438-470MHz) Transmitter Power Amplifier ...............................................2-2 3.1 First Power Controller Stage...........................................................................2-2 3.2 Power Controlled Driver Stage .......................................................................2-3 3.3 Final Stage......................................................................................................2-3 3.4 Directional Coupler.........................................................................................2-3 3.5 Antenna Switch...............................................................................................2-3 3.6 Harmonic Filter ...............................................................................................2-4 3.7 Power Control.................................................................................................2-4 4.0 UHF (438-470MHz) Frequency Synthesis ..........................................................2-4 4.1 Reference Oscillator .......................................................................................2-4 4.2 Fractional-N Synthesizer ................................................................................2-5 4.3 Voltage Controlled Oscillator (VCO) ...............................................................2-6 4.4 Synthesizer Operation ....................................................................................2-7 5.0 Controller Theory of Operation ............................................................................2-8 5.1 Radio Power Distribution ................................................................................2-8 5.2 Protection Devices........................................................................................ 2-10 5.3 Automatic On/Off ..........................................................................................2-10 5.4 Microprocessor Clock Synthesiser ...............................................................2-11 5.5 Serial Peripheral Interface (SPI)...................................................................2-12 5.6 SBEP Serial Interface................................................................................... 2-12 5.7 General Purpose I/O.....................................................................................2-12 5.8 Normal Microprocessor Operation................................................................2-13 5.9 Static Random Access Memory....................................................................2-14 6.0 Control Board Audio and Signalling Circuits ......................................................2-14 6.1 Audio Signalling Filter IC and Compander (ASFIC CMP) ............................2-14 7.0 Transmit Audio Circuits......................................................................................2-15 7.1 Microphone Input Path .................................................................................2-15 7.2 PTT Sensing and TX Audio Processing ....................................................... 2-16 iv 8.0 Transmit Signalling Circuits ............................................................................... 2-17 8.1 Sub-Audio Data (PL/DPL) ............................................................................ 2-17 8.2 High Speed Data .......................................................................................... 2-18 8.3 Dual Tone Multiple Frequency (DTMF) Data ............................................... 2-18 9.0 Receive Audio Circuits....................................................................................... 2-19 9.1 Squelch Detect ............................................................................................. 2-19 9.2 Audio Processing and Digital Volume Control.............................................. 2-20 9.3 Audio Amplification Speaker (+) Speaker (-) ................................................ 2-20 9.4 Handset Audio.............................................................................................. 2-21 9.5 Filtered Audio and Flat Audio ....................................................................... 2-21 10.0 Receive Audio Circuits ..................................................................................... 2-21 10.1 Sub-Audio Data (PL/DPL) and High Speed Data Decoder .......................... 2-21 10.2 Alert Tone Circuits........................................................................................ 2-22 Chapter 3 TROUBLESHOOTING CHARTS 1.0 Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2)................................ 3-2 1.1 Troubleshooting Flow Chart for Receiver (Sheet 2 of 2) ................................ 3-3 2.0 Troubleshooting Flow Chart for 25W Transmitter (Sheet 1 of 3) ....................... 3-4 2.1 Troubleshooting Flow Chart for 25W Transmitter (Sheet 2 of 3) ................... 3-5 2.2 Troubleshooting Flow Chart for 25W Transmitter (Sheet 3 of 3).................... 3-6 3.0 Troubleshooting Flow Chart for Synthesizer ....................................................... 3-7 4.0 Troubleshooting Flow Chart for VCO................................................................... 3-8 5.0 Troubleshooting Flow Chart for DC Supply (Sheet 1 of 2) .................................. 3-9 5.1 Troubleshooting Flow Chart for DC Supply (Sheet 2 of 2) ........................... 3-10 Chapter 4 UHF PCB/SCHEMATICS/PARTS LISTS 1.0 Allocation of Schematics and Circuit Boards ....................................................... 4-1 1.1 UHF2 and Controller Circuits ......................................................................... 4-1 2.0 UHF2 1-25W PCB 8488978U01 (Rev. D) / Schematics...................................... 4-3 2.1 UHF2 1-25W PCB 8488978U01 (Rev. D) Parts List .................................... 4-19 Chapter 1 MODEL CHART AND TECHNICAL SPECIFICATIONS 1.0 CM140/CM340/CM160/CM360 Model Chart CM Series UHF2 438-470MHz Model Description MDM50RNC9AA2_N CM140 438-470 MHz 1-25W 8-Ch MDM50RNC9AN2_N CM340 438-470 MHz 1-25W 10-Ch MDM50RNF9AA2_N MDM50RNF9AN2_N CM160 438-470 MHz 1-25W 64-Ch CM360 438-470 MHz 1-25W 100-Ch Item X X X X X X X X X Description FUE1021_ S. Tanapa UHF2 25W 8 Ch BNC PMUE2019_ S. Tanapa UHF2 25W 10 Ch BNC PMUE1999_ S. Tanapa UHF2 25W 64 Ch BNC PMUE2021_ S. Tanapa UHF2 25W 100 Ch BNC FCN6288_ Control Head X X FCN5523_ Control Head X X HKN4137_ Battery Power Cable X RMN50188_ HMN3596_ Mag One Microphone Compact Microphone X X X X X X GLN7324_ Low Profile Trunnion X X X X 6866546D02_ RTTE Leaflet X X X X 6866537D37_ Safety Leaflet FLE1621AS Servicing Kit CM140 PMUE2041AS Servicing Kit CM340 PMUE2027AS Servicing Kit CM160 PMUE2043AS Servicing Kit CM360 X X X X X = Indicates one of each is required 1-2 2.0 MODEL CHART AND TECHNICAL SPECIFICATIONS Technical Specifications Data is specified for +25°C unless otherwise stated. General Specification Frequency Range: Frequency Stability (-30°C to +60°C, 25°C Ref.) Channel Capacity: Channel Spacing: UHF2 438-470 MHz ±2 PPM CM140 - 8 CM340 - 10 CM160 - 64 CM360 - 100 12.5/20/25 kHz Power Output: 1-25W Power Supply: 13.2Vdc (10.8 - 15.6 Vdc) negative vehicle ground Dimensions (L X W X H) Weight: Low power (1-25W) 118mm X 169mm X 44mm 1.02 Kg Operating Temperature -30 to 60 o C Storage temperature -40 to 80o C Shock and Vibration Meets MIL-STD 810-C,D&E and TIA/EIA 603 Dust Meets MIL-STD 810-C,D&E and TIA/EIA 603 Humidity Meets MIL-STD 810-C,D&E and TIA/EIA 603 Technical Specifications 1-3 Transmitter Specification UHF2 Frequency Stability: +/- 2.5ppm Modulation Limiting: ±2.5 kHz @ 12.5 kHz ±4.0 kHz @ 20 kHz ±5.0 kHz @ 20/25 kHz Current Drain Transmit: 8A (25W) FM Hum and Noise: -35 dB@12.5 kHz -40 dB@ 20/25 kHz Conducted/Radiated Emissions: -36 dBm < 1 GHz -30 dBm > 1 GHz Adjacent Channel Power -60dB @12.5, -70dB @ 20/25kHz Audio Response: ( 300 to 3000Hz) +1, -3dB Audio Distortion: @ 1000 Hz, 60% Rated Maximum Deviation: 3% Typical Receiver Specification Sensitivity (12dBSINAD): (ETS) Intermodulation : (ETS) Adjacent Channel Selectivity: (ETS) Spurious Rejection: (ETS) Rated Audio: (ETS) (Extended audio with 4 Ohm speaker) Audio Distortion @ Rated Audio: UHF2 0.35µV (12.5kHz) 0.30µV (25kHz) Typical >65dB 70 dB @ 25 kHz 60 dB @ 12.5 kHz 70 dB 4W Internal , 13W External 3% Typical Hum and Noise: -35 dB @ 12.5 kHz -40 dB @ 20/25 kHz Audio Response: ( 300 to 3000Hz) +1, -3dB Conducted Spurious Emission per FCC Part 15: -57 dBm <1 GHz -47 dBm >1 GHz *Availability subject to the laws and regulations of individual countries. 1-4 MODEL CHART AND TECHNICAL SPECIFICATIONS Chapter 2 THEORY OF OPERATION 1.0 Introduction This Chapter provides a detailed theory of operation for the UHF circuits in the radio. Details of the theory of operation and trouble shooting for the the associated Controller circuits are included in this Section of the manual. 2.0 UHF (438-470MHz) Receiver 2.1 Receiver Front-End The received signal is applied to the radio’s antenna input connector and routed through the harmonic filter and antenna switch. The insertion loss of the harmonic filter/antenna switch is less than 1 dB. The signal is routed to the first filter (4-pole), which has an insertion loss of 2 dB typically. The output of the filter is matched to the base of the LNA (Q303) that provides a 16 dB gain and a noise figure of better than 2 dB. Current source Q301 is used to maintain the collector current of Q303. Diode CR301 protects Q303 by clamping excessive input signals. Q303 output is applied to the second filter (3-pole) which has an insertion loss of 1.5 dB. In Distance mode, Q304 turns on and causes D305 to conduct, thus bypassing C322 and R337. In Local mode, the signal is routed through C322 and R337, thus inserting 7 dB attenuation. Since the attenuator is located after the RF amplifier, the receiver sensitivity is reduced only by 6 dB, while the overall third order input intercept is raised. The first mixer is a passive, double-balanced type, consisting of T300, T301 and U302. This mixer provides all of the necessary rejection of the half-IF spurious response. High-side injection at +15 dBm is delivered to the first mixer. The mixer output is then connected to a duplex network which matches its output to the XTAL filter input (FL300) at the IF frequency of 44.85 MHz. The duplex network terminates into a 50 ohm resistor (R340) at all other frequencies. Antenna Front Filter 12.5kHzFilter LNA Second Filter Mixer 4- Pole Xtal Filter IF Amp 25kHzFilter First LO 25kHzFilter IFIC 2nd LO Xtal Osc Phase Shift Element Controller Figure 2-1 UHF Receiver Block Diagram 2-2 THEORY OF OPERATION 2.2 Receiver Back End The IF signal from the crystal filter enters the IF amplifier which provides 20 dB of gain and feeds the IF IC at pin 1. The first IF signal at 44.85 MHz mixes with the second local oscillator (LO) at 44.395 MHz to produce the second IF at 455 kHz. The second LO uses the external crystal Y301. The second IF signal is amplified and filtered by two external ceramic filters (FL303/FL302 for 12.5KHz channel spacing and FL304/FL301 for 25KHz channel spacing). The IF IC demodulates the signal by means of a quadrature detector and feeds the detected audio (via pin 7) to the audio processing circuits. At IF IC pin 5, an RSSI signal is available with a dynamic range of 70 dB. 3.0 UHF Transmitter Power Amplifier (438-470 MHz) The radio’s 25W PA is a three-stage amplifier used to amplify the output from the VCOBIC to the radio transmit level. All three stages utilize LDMOS technology. The gain of the first stage (U101) is adjustable and controlled by pin 7 of U103-2 via U103-3. It is followed by an LDMOS stage Q105 and LDMOS final stage Q100. Pin Diode Antenna Switch From VCO Controlled Stage PA Driver PA-Final Stage Antenna Harmonic Filter RF Jack Coupler Bias Forward A S FI C _C M P SPI BUS PA PWR SET L oo p C ont r ol le r U 103 - 2 Temperature Sense Figure 2-2 UHF Transmitter Block Diagram Devices U101, Q105 and Q100 are surface mounted. A metal clip ensures good thermal contact between both the driver and final stage, and the chassis. 3.1 First Power Controller Stage The first stage (U101) is a 20dB gain integrated circuit containing two LDMOS FET amplifier stages. It amplifies the RF signal from the VCO (TX_INJ). The output power of stage U101 is controlled by a DC voltage applied to pin 1 from the op-amp U103-3, pin 8. The control voltage simultaneously varies the bias of two FET stages within U101. This biasing point determines the overall gain of U101 and therefore its output drive level to Q105, which in turn controls the output power of the UHF Transmitter Power Amplifier (438-470 MHz) 2-3 PA.Op-amp U103-3 monitors the drain current of U101 via resistor R122 and adjusts the bias voltage of U101. In receive mode, the DC voltage from RX_EN line turns on Q101, which in turn switches off the biasing voltage to U101. 3.2 Power Controlled Driver Stage The next stage is an LDMOS device (Q105) which provides a gain of 12dB. This device requires a positive gate bias and a quiescent current flow for proper operation. The bias is set during transmit mode by the drain current control op-amp U102-1, and fed to the gate of Q105 via the resistive network R175, R147. Op-amp U102-1 monitors the drain current of Q105 via resistors R126-8 and adjusts the bias voltage of Q105. In receive mode the DC voltage from RX_EN line turns on Q102, which in turn switches off the biasing voltage to Q105. 3.3 Final Stage The final stage is an LDMOS device (Q100) providing a gain of 12dB. This device also requires a positive gate bias and a quiescent current flow for proper operation. The voltage of the line PA_BIAS is set in transmit mode by the ASFIC and fed to the gate of Q100 via the resistive network R134, R131. This bias voltage is tuned in the factory. If the transistor is replaced, the bias voltage must be tuned using the Tuner. Care must be taken not to damage the device by exceeding the maximum allowed bias voltage. The device’s drain current is drawn directly from the radio’s DC supply voltage input, B+, via L117 and L115. A matching network consisting of C1004-5, C1008, C1021: and two striplines, transforms the impedance to 50 ohms and feeds the directional coupler. 3.4 Directional Coupler The directional Coupler is a microstrip printed circuit, which couples a small amount of the forward power of the RF power from Q100.The coupled signal is rectified to an output power which is proportional to the DC voltage rectified by diode D105; and the resulting DC voltage is routed to the power control section to ensure that the forward power out of the radio is held to a constant value. 3.5 Antenna Switch The antenna switch utilizes the existing dc feed (B+) to the last stage device (Q100). The basic operation is to have both PIN diodes (D103, D104) turned on during key-up by forward biasing them. This is achieved by pulling down the voltage at the cathode end of D104 to around 12.4V (0.7V drop across each diode). The current through the diodes needs to be set around 100 mA to fully open the transmit path through resistor R108. Q106 is a current source controlled by Q103 which is turned on in Tx mode by TX_EN. VR102 ensures that the voltage at resistor R107 never exceeds 5.6V. 2-4 3.6 THEORY OF OPERATION Harmonic Filter Inductors L111 and L113 along with capacitors C1011, C1023, C1020 and C1016 form a low-pass filter to attenuate harmonic energy coming from the transmitter. Resistor R150 along with L126 drains any electrostatic charges that might otherwise build up on the antenna. The harmonic filter also prevents high level RF signals above the receiver passband from reaching the receiver circuits to improve spurious response rejection. 3.7 Power Control The output power is regulated by using a forward power detection control loop. A directional coupler samples a portion of the forward and reflected RF power. The forward sampled RF is rectified by diode D105, and the resulting DC voltage is routed to the operational amplifier U100. The error output current is then routed to an integrator, and converted into the control voltage. This voltage controls the bias of the pre-driver (U101 and driver (Q105) stages. The output power level is set by way of a DAC, PWR_SET, in the audio processing IC (U504) which acts at the forward power control loop reference. The sampled reflected power is rectified by diode D107,The resulting DC voltage is amplified by an operational amplifier U100 and routed to the summing junction. This detector protects the final stage Q100 from reflected power by increasing the error current. The temperature sensor protects the final stage Q100 from overheating by increasing the error current. A thermistor RT100 measures the final stage Q100 temperature. The voltage divider output is routed to an operational amplifier U103 and then goes to the summing junction. The Zener Diode VR101 keeps the loop control voltage below 5.6V and eliminates the DC current from the 9.3 regulator U501. Two local loops for the Pre Driver (U101) and for the Driver (Q105) are used in order to stabilize the current for each stage. In Rx mode, the two transistors Q101 and Q102 go to saturation and shut down the transmitter by applying ground to the Pre Driver U101 and for the Driver Q105 control. 4.0 UHF (438-470MHz) Frequency Synthesis The synthesizer consists of a reference oscillator (Y201), low voltage Fractional-N (LVFRAC-N) synthesizer (U200), and a voltage controlled oscillator (VCO) (U201). 4.1 Reference Oscillator The reference oscillator is a crystal (Y201) controlled Colpitts oscillator and has a frequency of 16.8MHz. The oscillator transistor and start-up circuit are located in the LVFRAC-N (U200) while the oscillator feedback capacitors, crystal, and tuning varactors are external. An analog-to-digital (A/D) converter internal to the LVFRAC-N (U200) and controlled by the microprocessor via SPI sets the voltage at the warp output of U200 pin 25. This sets the frequency of the oscillator. Consequently, the output of the crystal Y201 is applied to U200 pin 23. The method of temperature compensation is to apply an inverse Bechmann voltage curve, which matches the crystal’s Bechmann curve to a varactor that constantly shifts the oscillator back on frequency. The crystal vendor characterizes the crystal over a specified temperature range and codes this information into a bar code that is printed on the crystal package. In production, this crystal code is read via a 2-dimensional bar code reader and the parameters are saved. UHF (438-470MHz) Frequency Synthesis 2-5 This oscillator is temperature compensated to an accuracy of +/-2.5 PPM from -30 to 60 degrees C. The temperature compensation scheme is implemented by an algorithm that uses five crystal parameters (four characterize the inverse Bechmann voltage curve and one for frequency accuracy of the reference oscillator at 25 degrees C). This algorithm is implemented by the LVFRAC-N (U200) at the power up of the radio. TCXO Y200, along with its corresponding circuitry R204, R205, R210, and C2053, are not placed as the temperature compensated crystal proved to be reliable. 4.2 Fractional-N Synthesizer The LVFRAC-N U200 consists of a pre-scaler, programmable loop divider, control divider logic, phase detector, charge pump, A/D converter for low frequency digital modulation, balanced attenuator used to balance the high and low frequency analog modulation, 13V positive voltage multiplier, serial interface for control, and a super filter for the regulated 5 volts. DATA (U403 PIN 100) CLOCK (U403 PIN 1) CSX (U403 PIN 2) MOD IN (U501 PIN 40) +5V (U503 PIN 1) +5V (U503 PIN 1) 7 8 9 10 13, 30 5, 20, 34, 36 REFERENCE OSCILLATOR 23 24 VOLTAGE MULTIPLIER FREFOUT CLK GND CEX MODIN VCC, DC5V IOUT IADAPT VDD, DC5V MODOUT XTAL1 U200 XTAL2 FRACTIONAL-N SYNTHESIZER 25 WARP 32 PREIN 47 LOCK DATA LOW VOLTAGE VCP VMULT2 14 15 48 43 45 LOOP FILTER STEERING LINE 41 AUX3 2 AUX1 BIAS2 FREF (U504 PIN 34) 6, 22, 33, 44 3 1 (NU) BIAS1 LOCK (U403 PIN 56) 19 AUX4 AUX2 SFOUT VMULT1 4 VCO Bias LO RF INJECTION TRB VOLTAGE 28 FILTERED 5V CONTROLLED OSCILLATOR 40 TX RF INJECTION (1ST STAGE OF PA) 39 BWSELECT To IF Section PRESCALER IN Figure 2-3 UHF Synthesizer Block Diagram A voltage of 5V applied to the super filter input (U200, pin 30) supplies an output voltage of 4.5Vdc (VSF) at U200, pin 28. This supplies 4.5 V to the VCO Buffer IC U201. To generate a high voltage to supply the phase detector (charge pump) output stage at pin VCP (U200, pin 47) while using a low voltage 3.3Vdc supply, a 13V positive voltage multiplier is used (D200, D201, and capacitors C2024, 2025, 2026, 2055, 2027, 2001). Output lock (U200, pin 4) provides information about the lock status of the synthesizer loop. A high level at this output indicates a stable loop. A 16.8 MHz reference frequency is provided at U200, pin 19. 2-6 THEORY OF OPERATION 4.3 Voltage Controlled Oscillator (VCO) The Voltage Controlled Oscillator (VCO) consists of the VCO/Buffer IC (VCOBIC, U201), the TX and RX tank circuits, the external RX buffer stages, and the modulation circuitry. AUX3 (U200 Pin 2) Prescaler Out TRB IN Pin 20 Rx-SW Pin7 Tx-SW Pin13 (U200 Pin 28) Pin 19 U200 Pin 32 Pin 12 TX/RX/BS Switching Network Vcc-Superfilter Pin3 LO RF INJECTION Presc U201 VCOBIC Q200 Buffers Low Pass Filter Collector/RF in Steer Line Voltage (VCTRL) Pin4 RX Tank RX VCO Circuit TX VCO Circuit Rx Active Bias Pin5 Pin6 TX Tank RX RX Pin8 Pin14 TX Tx Active Bias Pin16 Pin15 TX Pin10 Vcc-Logic TX RF Injection Attenuator Vsens Circuit Pin18 (U200 Pin28) VCC Buffers Pin2 Pin1 Rx-I adjust Tx-I adjust Pins 9,11,17 (U200 Pin 28) Figure 2-4 UHF VCO Block Diagram The VCOBIC together with the LVFRAC-N (U200) generate the required frequencies in both transmit and receive modes. The TRB line (U201, pin 19) determines which VCO and buffer is enabled (high being TX output at pin 10, low being RX output at pin 8). A sample of the signal from the enabled output is routed from U201, pin 12 (PRESC_OUT), via a low pass filter to U200, pin 32 (PREIN). A steering line voltage between 3.0V and 10.0V at varactor D204 tunes the TX VCO through the frequency range of 438-470MHz, and at D203 tunes the RX VCO through the frequency range of 393.15-425.15MHz. The external RX amplifier is used to increase the output from U201, pin 9 from 3-4 dBm to the required 15dBm for proper mixer operation. In TX mode, the modulation signal from the LVFRAC-N (U200, pin 41) is applied to the VCO by way of the modulation circuit D205, R212, R211, C2073. UHF (438-470MHz) Frequency Synthesis 4.4 2-7 Synthesizer Operation The synthesizer consists of a low voltage FRAC-N IC (LVFRAC-N), reference oscillator, charge pump circuits, loop filter circuit, and DC supply. The output signal (PRESC_OUT) of the VCOBIC (U201, pin 12) is fed to the PREIN, pin 32 of U200 via a low pass filter which attenuates harmonics and provides a correct input level to the LVFRAC-N in order to close the synthesizer loop. The pre-scaler in the synthesizer (U200) is a dual modulus pre-scaler with selectable divider ratios. The divider ratio of the pre-scaler is controlled by the loop divider, which in turn receives its inputs via the SPI. The output of the pre-scaler is applied to the loop divider. The output of the loop divider is connected to the phase detector, which compares the loop divider’s output signal with the reference signal. The reference signal is generated by dividing down the signal of the reference oscillator (Y201). The output signal of the phase detector is a pulsed dc signal that is routed to the charge pump. The charge pump outputs a current from U200, pin 43 (IOUT). The loop filter (consisting of R224, R217, R234, C2074, C2075, C2077, C2078, C2079, C2080, C2028, and L205) transforms this current into a voltage that is applied the varactor diodes D203 and D204 for RX and TX respectively. The output frequency is determined by this control voltage. The current can be set to a value fixed in the LVFRAC-N or to a value determined by the currents flowing into BIAS 1 (U200, pin 40) or BIAS 2 (U200, pin 39). The currents are set by the value of R200 or R206 respectively. The selection of the three different bias sources is done by software programming. To modulate the synthesizer loop, a two-spot modulation method is utilized via the MODIN (U200, pin 10) input of the LVFRAC-N. The audio signal is applied to both the A/D converter (low frequency path) and the balance attenuator (high frequency path). The A/D converter converts the low frequency analog modulating signal into a digital code which is applied to the loop divider, thereby causing the carrier to deviate. The balance attenuator is used to adjust the VCO’s deviation sensitivity to high frequency modulating signals. The output of the balance attenuator is presented at the MODOUT port of the LVFRAC-N (U200,pin 41) and connected to the VCO modulation varactor D205. 2-8 5.0 THEORY OF OPERATION Controller Theory of Operation This section provides a detailed theory of operation for the radio and its components. The main radio is a single-board design, consisting of the transmitter, receiver, and controller circuits. A control head is connected by an extension cable. The control head contains LED indicators, a microphone connector, buttons, and speaker. In addition to the power cable and antenna cable, an accessory cable can be attached to a connector on the rear of the radio. The accessory cable enables you to connect accessories to the radio, such as an external speaker, emergency switch, foot-operated PTT, and ignition sensing, etc. External Microphone To Synthesizer Mod Out 16.8 MHz Reference Clock from Synthesizer Audio/Signaling Architecture Disc Audio ASFIC_CMP . Internal Microphone External Speaker Audio PA Internal Speaker µP Clock SPI To RF Section Digital Architecture SCI to Accessory & Control Head Connector RAM EEPROM 3.3V Regulator HC11FL0 FLASH Figure 2-5 Controller Block Diagram 5.1 Radio Power Distribution Voltage distribution is provided by five separate devices: ■ U514 P-cH FET - Batt + (Ext_SWB+) ■ U501 LM2941T - 9.3V ■ U503 LP2951CM - 5V ■ U508 MC 33269DTRK - 3.3V ■ U510 LP2986ILDX - 3.3V Digital Handset Controller Theory of Operation 2-9 The DC voltage applied to connector P2 supplies power directly to the following circuitry: ■ Electronic on/off control ■ RF power amplifier ■ 12 volts P-cH FET -U514 ■ 9.3 volt regulator ■ Audio PA Ignition Auto On/Off Switch Control B+ Control Head RF_PA Audio_PA Mic Connector Ferrite Bit Filt_B+ Antenna Switch Power Control 500mA FET P-CH On/Off Control SW_Filt_B+ 11-16.6V 0.9A Status LEDs 7_Seg 7_Seg DOT Bed to 7-Seg Back light Shift Reg Acces Conn Audio PA_Soutdown Power Loop Op_Amp 9.3V 65mA U501 9.3V Regulator Keypad Mic Bias 9V, 5mA 0.85A Reset 9.3V 45mA On/Off Control U503 5V RF Regulator 500mA Rx_Amp PA_Pre-driver PA Driver 3.2V 72mA 45mA LVFRAC_N IF_Amp 9.3V 75mA 9.3V 162mA U508 3.3V RF Reg 50mA 25mA ASFIC_CMP IFIC RX Cct U510 3.3V D Reg 90mA micro P RAM Flash EEPROM Figure 2-6 DC Power Distribution Block Diagram Regulator U501 is used to generate the 9.3 volts required by some audio circuits, the RF circuitry and power control circuitry. Input and output capacitors are used to reduce high frequency noise. Resistors R5001 / R5081 set the output voltage of the regulator. This regulator output is electronically enabled by a 0 volt signal on pin 2. Q502, Q505 and R5038 are used to disable the regulator when the radio is turned off. Voltage regulator U510 provides 3.3 volts for the digital circuitry. Operating voltage is from the regulated 9.3V supply. Input and output capacitors are used to reduce high frequency noise and provide proper operation during battery transients. U510 provides a reset output that goes to 0 volts if the regulator output goes below 3.1 volts. This is used to reset the controller to prevent improper operation. Voltage regulator U508 provides 3.3V for the RF circuits and ASFIC_CMP. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. 2-10 THEORY OF OPERATION Voltage regulator U503 provides 5V for the RF circuits. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. VSTBY is used only for CM360 5-tone radios. The voltage VSTBY, which is derived directly from the supply voltage by components R5103 and VR502, is used to buffer the internal RAM. Capacitor C5120 allows the battery voltage to be disconnected for a couple of seconds without losing RAM parameters. Dual diode D501 prevents radio circuitry from discharging this capacitor. When the supply voltage is applied to the radio, C5120 is charged via R5103 and D501. 5.2 Protection Devices Diode VR500 acts as protection against ESD, wrong polarity of the supply voltage, and load dump. VR692 - VR699 are for ESD protection. 5.3 Automatic On/Off The radio can be switched ON in any one of the following three ways: 5.3.1 ■ On/Off switch. (No Ignition Mode) ■ Ignition and On/Off switch (Ignition Mode) ■ Emergency No Ignition Mode When the radio is connected to the car battery for the first time, Q500 will be in saturation, Q503 will cut-off, Filt_B+ will pass through R5073, D500, and S5010-pin 6 (On/Off switch). When S5010 is ON, Filt_B+ will pass through S5010-pin5, D511, R5069, R5037 and base of Q505 and move Q505 into saturation. This pulls U501-pin2 through R5038, D502 to 0.2V and turns On U514 and U501 9.3V regulator which supplies voltage to all other regulators and consequently turns the radio on, When U504 (ASFIC_CMP) gets 3.3V, GCB2 goes to 3.3V and holds Q505 in saturation, for soft turn off. 5.3.2 Ignition Mode When ignition is connected for the first time, it will force high current through Q500 collector, This will move Q500 out of saturation and consequently Q503 will cut-off. S5010 pin 6 will get ignition voltage through R601 (for load dump), R610, (R610 & C678 are for ESD protection), VR501, R5074, and D500. When S5010 is ON, Filt_B+ passes through S5010-pin 5, D511, R5069, R5037 and base of Q505 and inserts Q505 into saturation. This pulls U501-pin 2 through R5038, D502 to 0.2V and turns on U514 and U501 9.3V regulator which supply voltage to all other regulators and turns the radio on, When U504 (ASFIC_CMP) get 3.3V supply, GCB2 goes to 3.3V and holds Q505 in saturation state to allow soft turn off, When ignition is off Q500, Q503 will stay at the same state so S5010 pin 6 will get 0V from Ignition, Q504 goes from Sat to Cut, ONOFF_SENSE goes to 3.3V and it indicates to the radio to soft turn itself by changing GCB2 to ‘0’ after de registration if necessary. Controller Theory of Operation 5.3.3 2-11 Emergency Mode The emergency switch (P1 pin 9), when engaged, grounds the base of Q506 via EMERGENCY _ACCES_CONN. This switches Q506 to off and consequently resistor R5020 pulls the collector of Q506 and the base of Q506 to levels above 2 volts. Transistor Q502 switches on and pulls U501 pin2 to ground level, thus turning ON the radio. When the emergency switch is released R5030 pulls the base of Q506 up to 0.6 volts. This causes the collector of transistor Q506 to go low (0.2V), thereby switching Q502 to off. While the radio is switched on, the µP monitors the voltage at the emergency input on the accessory connector via U403-pin 62. Three different conditions are distinguished: no emergency kit is connected, emergency kit connected (unpressed), and emergency press. If no emergency switch is connected or the connection to the emergency switch is broken, the resistive divider R5030 / R5049 will set the voltage to about 3.14 volts (indicates no emergency kit found via EMERGENCY_SENSE line). If an emergency switch is connected, a resistor to ground within the emergency switch will reduce the voltage on EMERGENCY _SENSE line, and indicate to the µP that the emergency switch is operational. An engaged emergency switch pulls line EMERGENCY _SENSE line to ground level. Diode VR503 limits the voltage to protect the µP input. While EMERGENCY _ACCES_CONN is low, the µP starts execution, reads that the emergency input is active through the voltage level of µP pin 64, and sets the DC POWER ON output of the ASFIC CMP pin 13 to a logic high. This high will keep Q505 in saturation for soft turn off. 5.4 Microprocessor Clock Synthesiser The clock source for the µP system is generated by the ASFIC CMP (U504). Upon power-up the synthesizer IC (FRAC-N) generates a 16.8 MHz waveform that is routed from the RF section to the ASFIC CMP pin 34. For the main board controller the ASFIC CMP uses 16.8 MHz as a reference input clock signal for its internal synthesizer. The ASFIC CMP, in addition to audio circuitry, has a programmable synthesizer which can generate a synthesized signal ranging from 1200Hz to 32.769MHz in 1200Hz steps. When power is first applied, the ASFIC CMP will generate its default 3.6864MHz CMOS square wave UP CLK (on U504 pin 28) and this is routed to the µP (U403 pin 90). After the µP starts operation, it reprograms the ASFIC CMP clock synthesizer to a higher UP CLK frequency (usually 7.3728 or 14.7456 MHz) and continues operation. The ASFIC CMP may be reprogrammed to change the clock synthesizer frequencies at various times depending on the software features that are executing. In addition, the clock frequency of the synthesizer is changed in small amounts if there is a possibility of harmonics of the clock source interfering with the desired radio receive frequency. The ASFIC CMP synthesizer loop uses C5025, C5024 and R5033 to set the switching time and jitter of the clock output. If the synthesizer cannot generate the required clock frequency it will switch back to its default 3.6864MHz output. Because the ASFIC CMP synthesizer and the µP system will not operate without the 16.8 MHz reference clock it (and the voltage regulators) should be checked first when debugging the system. 2-12 5.5 THEORY OF OPERATION Serial Peripheral Interface (SPI) The µP communicates to many of the IC’s through its SPI port. This port consists of SPI TRANSMIT DATA (MOSI) (U403-pin100), SPI RECEIVE DATA (MISO) (U403-pin 99), SPI CLK (U0403-pin1) and chip select lines going to the various IC’s, connected on the SPI PORT (BUS). This BUS is a synchronous bus, in that the timing clock signal CLK is sent while SPI data (SPI TRANSMIT DATA or SPI RECEIVE DATA) is sent. Therefore, whenever there is activity on either SPI TRANSMIT DATA or SPI RECEIVE DATA there should be a uniform signal on CLK. The SPI TRANSMIT DATA is used to send serial from a µP to a device, and SPI RECEIVE DATA is used to send data from a device to a µP. There are two IC’s on the SPI BUS, ASFIC CMP (U504 pin 22)), and EEPROM (U400). In the RF sections there is one IC on the SPI BUS, the FRAC-N Synthesizer. The chip select line CSX from U403 pin 2 is shared by the ASFIC CMP and FRAC-N Synthesizer. Each of these IC’s check the SPI data and when the sent address information matches the IC’s address, the following data is processed. When the µP needs to program any of these Is it brings the chip select line CSX to a logic “0” and then sends the proper data and clock signals. The amount of data sent to the various IC’s are different; e.g., the ASFIC CMP can receive up to 19 bytes (152 bits). After the data has been sent the chip select line is returned to logic “1”. 5.6 SBEP Serial Interface The SBEP serial interface allows the radio to communicate with the Customer Programming Software (CPS), or the Universal Tuner via the Radio Interface Box (RIB) or the cable with internal RIB. This interface connects to the SCI pin via control head connector (J2-pin 17) and to the accessory connector P1-6 and comprises BUS+. The line is bi-directional, meaning that either the radio or the RIB can drive the line. The µP sends serial data and it reads serial data via pin 97. Whenever the µP detects activity on the BUS+ line, it starts communication. 5.7 General Purpose Input/Output The controller provides six general purpose lines (PROG I/O) available on the accessory connector P1 to interface to external options. Lines PROG IN 3 and 6 are inputs, PROG OUT 4 is an output and PROG IN OUT 8, 12 and 14 are bi-directional. The software and the hardware configuration of the radio model define the function of each port. ■ PROG IN 3 can be used as external PTT input, or others, set by the CPS. The µP reads this port via pin 72 and Q412. ■ PROG OUT 4 can be used as external alarm output, set by the CPS. Transistor Q401 is controlled by the µP (U403 pin 55) ■ PROG IN 6 can be used as normal input, set by the CPS. The µP reads this port via pin 73 and Q411. This pin is also used to communicate with the RIB if resistor R421 is placed. ■ DIG IN OUT 8,12,14 are bi-directional and use the same circuit configuration. Each port uses an output Q416, Q404, Q405 controlled by µP pins 52, 53, 54. The input ports are read through µP pins 74, 76, 77; using Q409, Q410, Q411 Controller Theory of Operation 5.8 2-13 Normal Microprocessor Operation For this radio, the µP is configured to operate in one of two modes, expanded and bootstrap. In expanded mode the µP uses external memory devices to operate, whereas in bootstrap operation the µP uses only its internal memory. In normal operation of the radio the µP is operating in expanded mode as described below. During normal operation, the µP (U403) is operating in expanded mode and has access to 3 external memory devices; U400 (EEPROM), U402 (SRAM), U404 (Flash). Also, within the µP there are 3 Kilobytes of internal RAM, as well as logic to select external memory devices. The external EEPROM (U400) space contains the information in the radio which is customer specific, referred to as the codeplug. This information consists of items such as: 1) what band the radio operates in, 2) what frequencies are assigned to what channel, and 3) tuning information. The external SRAM (U402) as well as the µP’s own internal RAM space are used for temporary calculations required by the software during execution. All of the data stored in both of these locations is lost when the radio powers off. The µP provides an address bus of 16 address lines (ADDR 0 - ADDR 15), and a data bus of 8 data lines (DATA 0 - DATA 7). There are also 3 control lines; CSPROG (U403-38) to chip select U404-pin 30 (FLASH), CSGP2 (U403-pin 41) to chip select U404-pin 20 (SRAM) and PG7_R_W (U403-pin 4) to select whether to read or to write. The external EEPROM (U400-pin1). When the µP is functioning normally, the address and data lines should be toggling at CMOS logic levels. Specifically, the logic high levels should be between 3.1 and 3.3V, and the logic low levels should be between 0 and 0.2V. No other intermediate levels should be observed, and the rise and fall times should be <30ns. The low-order address lines (ADDR 0 - ADDR 7) and the data lines (DATA 0-DATA 7) should be toggling at a high rate, e.g., you should set your oscilloscope sweep to 1us/div. or faster to observe individual pulses. High speed CMOS transitions should also be observed on the µP control lines. On the µP the lines XIRQ (U403-pin 48), MODA LIR (U403-pin 58), MODB VSTPY (U403-pin 57) and RESET (U403-pin 94) should be high at all times during normal operation. Whenever a data or address line becomes open or shorted to an adjacent line, a common symptom is that the RESET line goes low periodically, with the period being in the order of 20ms. In the case of shorted lines you may also detect the line periodically at an intermediate level, i.e. around 2.5V when two shorted lines attempt to drive to opposite rails. The MODA LIR (U403-pin 58) and MODB VSTPY (U403-pin 57) inputs to the µP must be at a logic “1” for it to start executing correctly. After the µP starts execution it will periodically pulse these lines to determine the desired operating mode. While the Central Processing Unit (CPU) is running, MODA LIR is an open-drain CMOS output which goes low whenever the µP begins a new instruction. An instruction typically requires 2-4 external bus cycles, or memory fetches. There are eight analog-to-digital coverter ports (A/D) on U403 labelled within the device block as PEO-PE7. These lines sense the voltage level ranging from 0 to 3.3V of the input line and convert that level to a number ranging from 0 to 255 which is read by the software to take appropriate action. 2-14 5.9 THEORY OF OPERATION Static Random Access Memory (SRAM) The SRAM (U402) contains temporary radio calculations or parameters that can change very frequently, and which are generated and stored by the software during its normal operation. The information is lost when the radio is turned off. The device allows an unlimited number of write cycles. SRAM accesses are indicated by the CS signal U402 (which comes from U403-CSGP2) going low. U402 is commonly referred to as the external RAM as opposed to the internal RAM which is the 3 Kilobytes of RAM which is part of the 68HC11FL0. Both RAM spaces serve the purpose. However, the internal RAM is used for the calculated values which are accessed most often. Capacitor C402 and C411 serves to filter out any AC noise which may ride on +3.3 V at U402 6.0 Control Board Audio and Signalling Circuits 6.1 Audio Signalling Filter IC and Compander (ASFIC CMP) The ASFIC CMP (U504) used in the controller has the following four functions: 1. RX/TX audio shaping, i.e. filtering, amplification, attenuation 2. RX/TX signaling, PL/DPL/HST/MDC 3. Squelch detection 4. µP clock signal generation The ASFIC CMP is programmable through the SPI BUS (U504 pins-20/21/22), normally receiving 19 bytes. This programming sets up various paths within the ASFIC CMP to route audio and/or signaling signals through the appropriate filtering, gain and attenuator blocks. The ASFIC CMP also has 6 General Control Bits GCB0-5 which are CMOS level outputs and used for the following: ■ GCBO - BW Select ■ GCBI - switches the audio PA On/Off ■ GCB2 - DC Power On switches the voltage regulator (and the radio) on and off ■ GCB3 - Control on MUX U509 pin 9 to select between Low Cost Mic path to STD Mic Path ■ GCB4 - Control on MUX U509 pin 11 to select between Flat RX path to filtered RX path on the accessory connector. ■ GCB5 - Control on MUX U509 pin 10 to select between Flat TX path mute and Flat TX path Transmit Audio Circuits 7.0 2-15 Transmit Audio Circuits J2 24kOhms U509 15 MIC 46 35 P1 48 2 FLAT TX AUDIO MIC INT GCB3 MIC EXT U509 5 36 TX RTN MUX CONTROL HEAD CONNECTOR EXT MIC 44 TX SND 42 MUX AUX TX ACCESSORY CONNECTOR FILTERS AND PREEMPHASIS MIC ASFIC_CMP IN U504 LIMITER HS SUMMER SPLATTER FILTER LS SUMMER 38 GCB5 FLAT TX AUDIO MUTE VCO ATN ATTENUATOR MOD IN 40 TO RF SECTION (SYNTHESIZER) Figure 2-7 Transmit Audio Paths 7.1 Microphone Input Path The radio supports 2 distinct microphone paths known as internal (from control head J2-15) and external mic (from accessory connector P1-2) and an auxiliary path (FLAT TX AUDIO, from accessory connector P1-5). The microphones used for the radio require a DC biasing voltage provided by a resistive network. The two microphone audio input paths enter the ASFIC CMP at U504-pin 48 (external mic) and U504-pin 46 (internal mic). The microphone is plugged into the radio control head and connected to the audio DC via J2-pin 15. The signal is then routed via C5045 to MUX U509 that select between two paths with different gain to support Low Cost Mic (Mic with out amplifier in it) and Standard Mic. 7.1.1 Low Cost Microphone Hook Pin is shorted to Pin 1(9.3V) inside the Low Cost Mic, This routes 9.3V to R429, and creates 2.6V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 = ‘0’. The audio signal is routed from C5045 via U509-5 (Z0), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int. mic (C5046 100nF creates a159Hz pole with U504- 46 int mic impedance of 16Kohm). 2-16 7.1.2 THEORY OF OPERATION Standard Microphone Hook Pin is shorted to the hook mic inside the standard Mic, If the mic is out off hook, 3.3V is routed to R429 via R458, D401, and it create 0.7V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 =‘1’. The audio signal is routed from C5045 via U509-3 (Z1), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int mic (C5046 100nF create a159Hz pole with U504- 46 int mic impedance of 16Kohm). 9.3VDC is routed via R5077, R5075 to J2-15, It create 4.65V with Mic Impedance. C5010 supplies AC Ground to create AC impedance of 510 Ohms via R5075. and Filter 9.3V DC mic bias supply. Note: The audio signal at U504-pin 46 should be approximately 12mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The external microphone signal enters the radio on accessory connector P1 pin 2 and is routed via line EXT MIC to R5054. R5078 and R5076 provide the 9.3Vdc bias. Resistive divider R5054/ R5070 divide the input signal by 5.5 and provide input protection for the CMOS amplifier input. R5076 and C5009 provide a 510 ohm AC path to ground that sets the input impedance for the microphone and determines the gain based on the emitter resistor in the microphone’s amplifier circuit. C5047 serves as a DC blocking capacitor. The audio signal at U504-pin 48 should be approximately 14mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The FLAT TX AUDIO signal from accessory connector P1-pin 5 is fed to the ASFIC CMP (U504 pin 42 through U509 pin 2 to U509 pin 15 via U506 OP-AMP circuit and C5057. The ASFIC has an internal AGC that can control the gain in the mic audio path. The AGC can be disabled / enabled by the µP. Another feature that can be enabled or disabled in the ASFIC is the VOX. This circuit, along with Capacitor C5023 at U504-pin 7, provides a DC voltage that can allow the µP to detect microphone audio. The ASFIC can also be programmed to route the microphone audio to the speaker for public address operation. 7.2 PTT Sensing and TX Audio Processing Internal microphone PTT is sensed by µP U403 pin 71. Radio transmits when this pin is “0” and selects inside the ASFIC_ CMP U504 internal Mic path. When the internal Mic PTT is “0” then external Mic PTT is grounded via D402. External Mic PTT is sensed by U403 pin 72 via Q412 circuits. The radio transmits when this pin is “0” and selects inside the ASFIC _CMP U504 External Mic path. Inside the ASFIC CMP, the mic audio is filtered to eliminate frequency components outside the 3003000Hz voice band, and pre-emphasized if pre-emphasis is enabled. The signal is then limited to prevent the transmitter from over deviating. The limited mic audio is then routed through a summer, which is used to add in signaling data, and then to a splatter filter to eliminate high frequency spectral components that could be generated by the limiter. The audio is then routed to an attenuator, which is tuned in the factory or the field to set the proper amount of FM deviation. The TX audio emerges from the ASFIC CMP at U504-pin 40 MOD IN, at which point it is routed to the RF section. Transmit Signalling Circuits 8.0 2-17 Transmit Signalling Circuits HS SUMMER 44 MICRO CONTROLLER U403 19 HIGH SPEED CLOCK IN (HSIO) DTMF ENCODER 82 SPI BUS SPLATTER FILTER ASFIC_CMP U504 85 80 5-3-2 STATE ENCODER 18 LOW SPEED CLOCK IN (LSIO) PL ENCODER LS SUMMER ATTENUATOR 40 MOD IN TO RF SECTION (SYNTHESIZER) Figure 2-8 Transmit Signalling Path From a hardware point of view, there are 3 types of signaling: ■ Sub-audible data (PL / DPL / Connect Tone) that gets summed with transmit voice or signaling, ■ DTMF data for telephone communication in trunked and conventional systems, and ■ Audible signaling including MDC and high-speed trunking. Note: All three types are supported by the hardware while the radio software determines which signaling type is available. 8.1 Sub-Audio Data (PL/DPL) Sub-audible data implies signaling whose bandwidth is below 300Hz. PL and DPL waveforms are used for conventional operation and connect tones for trunked voice channel operation. The trunking connect tone is simply a PL tone at a higher deviation level than PL in a conventional system. Although it is referred to as “sub-audible data”, the actual frequency spectrum of these waveforms may be as high as 250 Hz, which is audible to the human ear. However, the radio receiver filters out any audio below 300Hz, so these tones are never heard in the actual system. Only one type of sub-audible data can be generated by U504 (ASFIC CMP) at any one time. The process is as follows, using the SPI BUS, the µP programs the ASFIC CMP to set up the proper lowspeed data deviation and select the PL or DPL filters. The µP then generates a square wave which strobes the ASFIC PL / DPL encode input LSIO U504-pin 18 at twelve times the desired data rate. For example, for a PL frequency of 103Hz, the frequency of the square wave would be 1236Hz. This drives a tone generator inside U504 which generates a staircase approximation to a PL sine wave or DPL data pattern. This internal waveform is then low-pass filtered and summed with voice or data. The resulting summed waveform then appears on U504-pin 40 (MOD IN), where it is sent to the RF board as previously described for transmit audio. A trunking connect tone would be generated in the same manner as a PL tone. 2-18 8.2 THEORY OF OPERATION High Speed Data High speed data refers to the 3600 baud data waveforms, known as Inbound Signaling Words (ISWs) used in a trunking system for high speed communication between the central controller and the radio. To generate an ISW, the µP first programs the ASFIC CMP (U504) to the proper filter and gain settings. It then begins strobing U504-pin 19 (HSIO) with a pulse when the data is supposed to change states. U504’s 5-3-2 State Encoder (which is in a 2-state mode) is then fed to the postlimiter summer block and then the splatter filter. From that point it is routed through the modulation attenuator and then out of the ASFIC CMP to the RF board. MDC is generated in much the same way as trunking ISW. However, in some cases these signals may also pass through a data preemphasis block in the ASFIC CMP. Also these signaling schemes are based on sending a combination of 1200 Hz and 1800 Hz tones only. Microphone audio is muted during high speed data signaling. 8.3 Dual Tone Multiple Frequency (DTMF) Data DTMF data is a dual tone waveform used during phone interconnect operation. It is the same type of tones which are heard when using a “Touch Tone” telephone. There are seven frequencies, with four in the low group (697, 770, 852, 941Hz) and three in the high group (1209, 1336, 1477Hz). The high-group tone is generated by the µP (U403-46) strobing U50419 at six times the tone frequency for tones less than 1440Hz or twice the frequency for tones greater than 1440Hz. The low group tone is generated by the ASFIC CMP, controlled by the µP via SPI bus. Inside U504 the low-group and high-group tones are summed (with the amplitude of the high group tone being approximately 2 dB greater than that of the low group tone) and then preemphasized before being routed to the summer and splatter filter. The DTMF waveform then follows the same path as was described for high-speed data. Receive Audio Circuits 9.0 2-19 Receive Audio Circuits ACCESSORY CONNECTOR 11 1 AUDIO PA U502 9 4 SPKR + 16 SPKR - 1 EXTERNAL SPEAKER 6 INT SPKR+ INT SPKRCONTROL HEAD CONNECTOR 19 MUTE U509 FLT RX AUDIO P1 INTERNAL SPEAKER 20 J2 18 HANDSET AUDIO U505 37 39 10 GCB4 U IO 43 AUX RX 14 41 URX OUT AUDIO GCB1 VOLUME ATTEN. ASFIC_CMP U504 FILTER AND DEEMPHASIS DISC FROM AUDIO RF SECTION (IF IC) 2 DISC PL FILTER LIMITER LIMITER, RECTIFIER FILTER, COMPARATOR LS IO 18 SQUELCH CIRCUIT SQ DET CH ACT 16 17 84 83 MICRO CONTROLLER 80 U403 85 Figure 2-9 Receive Audio Paths 9.1 Squelch Detect The radio’s RF circuits are constantly producing an output at the discriminator (IF IC). This signal (DISC AUDIO) is routed to the ASFIC CMP’s squelch detect circuitry input DISC (U504-pin 2). All of the squelch detect circuitry is contained within the ASFIC CMP. Therefore from a user’s point of view, DISC AUDIO enters the ASFIC CMP, and the ASFIC CMP produces two CMOS logic outputs based on the result. They are CH ACT (U504-16) and SQ DET (U504-17). The squelch signal entering the ASFIC CMP is amplified, filtered, attenuated, and rectified. It is then sent to a comparator to produce an active high signal on CH ACT. A squelch tail circuit is used to produce SQ DET (U504-17) from CH ACT. The state of CH ACT and SQ DET is high (logic “1”) when carrier is detected, otherwise low (logic “0”). CH ACT is routed to the µP pin 84 while SQ DET is routed to the µP pin 83. SQ DET is used to determine all audio mute / unmute decisions except for Conventional Scan. In this case CH ACT is a pre-indicator as it occurs slightly faster than SQ DET. 2-20 9.2 THEORY OF OPERATION Audio Processing and Digital Volume Control The receiver audio signal (DISC AUDIO) enters the controller section from the IF IC where it is.DC coupled to ASFIC CMP via the DISC input U504-pin 2. The signal is then applied to both the audio and the PL/DPL paths The audio path has a programmable amplifier, whose setting is based on the channel bandwidth being received, an LPF filter to remove any frequency components above 3000Hz, and a HPF to strip off any sub-audible data below 300Hz. Next, the recovered audio passes through a deemphasis filter (if it is enabled to compensate for Pre-emphasis which is used to reduce the effects of FM noise). The IC then passes the audio through the 8-bit programmable attenuator whose level is set depending on the value of the volume control. Finally the filtered audio signal passes through an output buffer within the ASFIC CMP. The audio signal exits the ASFIC CMP at AUDIO output (U504 pin 41). The µP programs the attenuator, using the SPI BUS, based on the volume setting. The minimum / maximum settings of the attenuator are set by codeplug parameters. Since sub-audible signaling is summed with voice information on transmit, it must be separated from the voice information before processing. Any sub-audible signaling enters the ASFIC CMP from the IF IC at DISC U504-2. Once inside, it goes through the PL/DPL path. The signal first passes through one of the two low-pass filters, either the PL low-pass filter or the DPL/LST low-pass filter. Either signal is then filtered and goes through a limiter and exits the ASFIC CMP at LSIO (U504-pin 18). At this point, the signal will appear as a square wave version of the sub-audible signal which the radio received. The µP U403 pin 80 will decode the signal directly to determine if it is the tone / code which is currently active on that mode. 9.3 Audio Amplification Speaker (+) Speaker (-) The output of the ASFIC CMP’s digital volume pot, U504-pin 41 is routed through DC blocking capacitor C5049 to the audio PA (U502 pin 1 and 9). The audio power amplifier has one inverted and one non-inverted output that produces the differential audio output SPK+/SPK- (U502 pins 4 and 6) The audio PA is enabled via the ASFIC CMP (U504-GCB1). When the base of Q501 is low, the transistor is off and U502-pin 8 is high, using pull up resistor R5041, and the audio PA is ON. The voltage at U502-pin 8 must be above 8.5Vdc to properly enable the device. If the voltage is between 3.3 and 6.4V, the device will be active but has its input (U502-pins 1/9) off. This is a mute condition which is used to prevent an audio pop when the PA is enabled. The SPK+ and SPK- outputs of the audio PA have a DC bias which varies proportionately with B+ (U502- pin 7). B+ of 11V yields a DC offset of 5V, and B+ of 17V yields a DC offset of 8.5V. If either of these lines is shorted to ground, it is possible that the audio PA will be damaged. SPK+ and SPKare routed to the accessory connector (P1-pin 1 and 16) and to the control head (connector J2-pins 19 and 20). Receive Signalling Circuits 9.4 2-21 Handset Audio Certain handheld accessories have a speaker within them which require a different voltage level than that provided by U502. For these devices HANDSET AUDIO is available at control head connector J2 pin18. The received audio from the output of the ASFIC CMP’s digital volume attenuator is routed to U505 pin 2 where it is amplified. This signal is routed from the output of the op-amp U505 to J2-pin 18. From the control head, the signal is sent directly to the microphone jack. 9.5 Filtered Audio and Flat Audio The ASFIC CMP output audio at U504-pin 39 is filtered and de-emphasized, but has not gone through the digital volume attenuator. From ASFIC CMP U504-pin 39 the signal is routed via R5034 through gate U509-pin 12 and AC coupled to U505-pin 6. The gate controlled by ASFIC CMP port GCB4 selects between the filtered audio signal from the ASFIC CMP pin 39 (URXOUT) or the unfiltered (flat) audio signal from the ASFIC CMP pin 10 (UIO). Resistors R5034 and R5021 determine the gain of op-amp UU505-pin 6 for the filtered audio while R5032 and R5021 determine the gain for the flat Audio. The output of U505-pin 7 is then routed to P1 pin 11 via DC blocking capacitor C5003. Note that any volume adjustment of the signal on this path must be done by the accessory. 10.0 Receive Signalling Circuits DATA FILTER AND DEEMPHASIS DET AUDIO DISCRIMINATOR AUDIO FROM RF SECTION (IF IC) 2 LIMITER HSIO 19 82 44 DISC ASFIC_CMP U504 FILTER LIMITER MICRO CONTROLLER U403 LSIO 18 80 85 PLEAP 8 PLCAP2 25 Figure 2-10 Receive Signalling Paths 10.1 Sub-Audio Data (PL/DPL) and High Speed Data Decoder The ASFIC CMP (U504) is used to filter and limit all received data. The data enters the ASFIC CMP at input DISC (U504 pin 2). Inside U504 the data is filtered according to data type (HS or LS), then it is limited to a 0-3.3V digital level. The MDC and trunking high speed data appear at U504-pin 19, where it connects to the µP U403 pin 80. 2-22 THEORY OF OPERATION The low speed limited data output (PL, DPL, and trunking LS) appears at U504-pin18, where it connects to the µP U403-pin 80. The low speed data is read by the µP at twice the frequency of the sampling waveform; a latch configuration in the ASFIC CMP stores one bit every clock cycle. The external capacitors C5028, and C5026 set the low frequency pole for a zero crossings detector in the limiters for PL and HS data. The hysteresis of these limiters is programmed based on the type of received data. 10.2 Alert Tone Circuits When the software determines that it needs to give the operator an audible feedback (for a good key press, or for a bad key press), or radio status (trunked system busy, phone call, circuit failures), it sends an alert tone to the speaker. It does so by sending SPI BUS data to U504 which sets up the audio path to the speaker for alert tones. The alert tone itself can be generated in one of two ways: internally by the ASFIC CMP, or externally using the µP and the ASFIC CMP. The allowable internal alert tones are 304, 608, 911, and 1823Hz. In this case a code contained within the SPI BUS load to the ASFIC CMP sets up the path and determines the tone frequency, and at what volume level to generate the tone. (It does not have to be related to the voice volume setting.) For external alert tones, the µP can generate any tone within the 100-3000Hz audio band. This is accomplished by the µP generating a square wave which enters the ASFIC CMP at U504 pin 19. Inside the ASFIC CMP this signal is routed to the alert tone generator. The output of the generator is summed into the audio chain just after the RX audio de-emphasis block. Inside U504, the tone is amplified and filtered, then passed through the 8-bit digital volume attenuator, which is typically loaded with a special value for alert tone audio. The tone exits at U504pin 41 and is routed to the audio PA like receive audio. Chapter 3 TROUBLESHOOTING CHARTS This section contains detailed troubleshooting flowcharts. These charts should be used as a guide in determining the problem areas. They are not a substitute for knowledge of circuit operation and astute troubleshooting techniques. It is advisable to refer to the related detailed circuit descriptions in the theory of operation sections prior to troubleshooting a radio. Most troubleshooting charts end up by pointing to an IC to replace. It is not always noted, but it is good practice to verify supplies and grounds to the affected IC and to trace continuity to the malfunctioning signal and related circuitry before replacing any IC. For instance, if a clock signal is not available at a destination, continuity from the source IC should be checked before replacing the source IC. 3-2 1.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2) START Yes Problem in 12 KHz and 25 KHz channel spacing Go to DC Section 9V on Yes R310 (LNA) OK ? No Check RX_EN Go to DC Section No 3V to U301 Okay ? Yes Check Q306, Q300 and U403 Check Q304, D305 and U403 Go to SYN Section Go to DC Section No No RX_EN ON ? Yes LOC_DIST ON? Yes Check LOC_DIST Check TPI No LO POWER OK ? Yes Check 5V on R337 No 5V Yes (IF AMP) OK ? Check 3V on R339 Go to A Check D301-304 Replace IF Filters( FL304, FL301) If problem in 25 KHz spacing Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2) 1.1 3-3 Troubleshooting Flow Chart for Receiver (Sheet 2 of 2) From A 3V (IFIC -Vcc) OK ? Go to DC Section No Check the component No Antenna to Mixer circuitry problem No Check visually all receiver components installation ? Yes Installation OK ? Yes Inject - 40dBm (CW) to RF connector Check Power on C335 RF Yes Power > -28 dBM? Check Power on C337 Replace Q305, Q300, U302 Check passive components Replace Q303, Q301 Check passive components No Replace Y301 No Go to DC Section 3V to U301 OK? Yes Y301 OK ? No Yes RF Yes Power > -28 dBM? Replace Q302, Y300 Check D301 - 304 Replace U300 Check Y301 44.395 MHz 3-4 2.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 25W Transmitter (Sheet 1 of 3) START No or too low power when keyed Check components between Q100 and RF output, Antenna Switch D104, D103, VR102 and Q106 Before replacing Q100. >1A Current increase when keyed? >800mA & <1A <800mA Check PA Stages Yes Control Voltage at TP150 >1.6V? No Check 9.3V Regulator U501, R180 & R181 No Voltage U103 pin 5 = 4.7V? Yes Check power settings, tuning & components between U103 Pin 3 and ASFIC Pin 6 before replacing ASFIC No U103 Pin 3 <2.6Vdc Yes Check U103 Yes Short U100 Pin 3 to ground PA Bias Voltage@R134 >2Vdc No Check Forward Power Sense Circuit Check PA Stages Yes Voltage at TP150 rises? No Check Forward Power Sense Circuit Troubleshooting Flow Chart for 25W Transmitter (Sheet 1 of 3) 2.1 3-5 Troubleshooting Flow Chart for 25W Transmitter (Sheet 2 of 3) Check PA Stages No or too low power when keyed DC Voltage at Q101 & Q102 base=0? Check Q101, Q102, R153, R136, R165, R122, R168 & R137 <3.5V Yes Check U103 before replacing U101 DC Voltage at U103 Pin 8 >4.5V Check resistive network at Pin 9 and 10 of U103 before replacing U101 3.5 to 4.5V Measure DC Voltage at U102 Pin 1 <2V Pin 1 Voltage >3V Check Q102, R139, R155, R166, R126R128, R169, R138, R175, R147 No DC Voltage U102 Pin 3 = 8.7V Check U403 Yes No DC Voltage at U103 Pin 10=8.9V No 2-3V Yes Check U102 before replacing Q105 Check Final PA Stages Check resistive network at Pin 2 & 3 of U102 before replacing Q105 3-6 2.2 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 25W Transmitter (Sheet 3 of 3) Check Final PA Stage <2V Check Bias Tuning, R134, R131 & R106 before replacing ASFIC U504 PA_Bias Voltage at R134 Supply Voltage Replace Q100 2-3V RF Voltage after C1044 >100mV? No Check FGU Yes Voltage across R122 >50mV? No Check components between C1044 & C1117 No Check components between C1117 & Q105 No Check components between Q105 & Q100 Yes RF Voltage Q105 gate >250mV? Yes RF Voltage Q100 gate >3V? Yes Check components between Q100 & antenna connector Troubleshooting Flow Chart for Synthesizer 3.0 3-7 Troubleshooting Flow Chart for Synthesizer Start NO Correct Problem Check D200, D201, C2026, C2025, & C2027 5V at U200 pins 5, 20, 34 & 36 Visual check of the Board OK? NO Check 5V Regulator U503 YES YES YES 5V at pin 6 of D200 NO Is U200 Pin 47 at = 13VDC ? NO +5V at U200 Pin’s 13 & 30 ? NO YES Check R228 Check R201 Is U201 Pin 19 <40 mVDC in RX & >4.5 VDC in TX? (at VCO section) ? NO Are Waveforms at Pins 14 & 15 triangular ? NO YES NO NO Is there a short between Pin 47 and Pins 14 & 15 of U200 ? Check programming lines between U403 and U200 Pins 7,8 & 9 NO YES Remove Shorts Is RF level at U200 Pin 32 -12 < x <-25 dBm ? YES Replace U200 NO Replace U200 NO YES NO Replace U200 YES YES Check Y201 and associated Parts Are signals at Pin’s 14 &15 of U200 ? YES Is U200 Pin 2 >4.5 VDC in Tx & <40 mVDC in Rx ? Is 16.8MHz signal at U200 Pin 23? NO Check 5V Regulator U503 NO YES YES Is 16.8MHz Signal at U200 Pin 19 ? If C2052, R208,C2067, C2068, L210 are OK, then see VCO troubleshooting chart Check uP U403 Troubleshooting Chart Do Pins 7,8 & 9 of U200 toggle when channel is changed? YES Is information from mP U403 correct ? YES Replace U200 3-8 TROUBLESHOOTING CHARTS 4.0 Troubleshooting Flow Chart for VCO RX VCO Low or no RF Signal at input to PA Low or no RF Signal at TP1 Visual check of board OK? NO Correct Problem NO Visual check of board OK? YES YES Make sure Synthesizer is working correctly and runner between U200 Pin 28 and U201 Pin 14 & and is OK NO 4.5V DC at U201 Pin 14 & 18 OK ? 4.5V DC at U201 Pin 14&18 OK ? NO YES YES 35mV DC at U201 Pin 19 OK? TX VCO Check runner between U200 Pin 2 and U201 Pin 19 NO NO 4.8V DC at U201 Pin 19 OK? YES Is RF available at base of Q200 YES NO Are U201 Pins 13 at 4.4V 15 at 1.1V 10 at 4.5V 16 at 1.9V Replace U201 YES Are Q200 Base at 2.4V Collector at 4.5V Emitter at 1.7V If all parts associated with the pins are OK, replace U201 NO YES NO If all parts associated with the pins are OK, replace Q200 NO Is RF available at C2060 If parts between R109 & U201 Pin10 are OK, replace U201 YES YES Check parts to pre-driver If all parts from collector of Q200 to TP1 are OK, replace Q200 Power OK but no modulation Audio =180mVRMS at “-” Side of NO Replace R212 D205 YES 4.5VDC at D205 NO YES If R211 and R12 are OK, then replace D205 Replace R211 Troubleshooting Flow Chart for DC Supply (1 of 2) 5.0 3-9 Troubleshooting Flow Chart for DC Supply (1 of 2) Since the failure of a critical voltage supply might cause the radio to automatically power down, supply voltages should first be probed with a multimeter. If all the board voltages are absent, then the voltage test point should be retested using a rising-edge-triggered oscilloscope. If the voltage is still absent, then another voltage should be tested using the oscilloscope. If that voltage is present, then the original voltage supply in question is defective and requires investigation of associated circuitry. 5V Check VDC on C5006 Go to 3V Replace U503 Yes Yes V=5V ? 9v1 GHz Adjacent Channel Power -60dB @12.5, -70dB @ 20/25kHz Audio Response: ( 300 to 3000Hz) +1, -3dB Audio Distortion: @ 1000 Hz, 60% Rated Maximum Deviation: 3% Typical Receiver Specification Sensitivity (12dBSINAD): (ETS) Intermodulation : (ETS) Adjacent Channel Selectivity: (ETS) Spurious Rejection: (ETS) Rated Audio: (ETS) (Extended audio with 4 Ohm speaker) Audio Distortion @ Rated Audio: VHF2 0.35µV (12.5kHz) 0.30µV (25kHz) Typical >65dB 75 dB @ 25 kHz 65 dB @ 12.5 kHz 75 dB 4W Internal , 13W External 3% Typical Hum and Noise: -40 dB @ 12.5 kHz -45 dB @ 20/25 kHz Audio Response: ( 300 to 3000Hz) +1, -3dB Conducted Spurious Emission per FCC Part 15: -57 dBm <1 GHz -47 dBm >1 GHz *Availability subject to the laws and regulations of individual countries. 1-4 MODEL CHART AND TECHNICAL SPECIFICATIONS Chapter 2 THEORY OF OPERATION 1.0 Introduction This Chapter provides a detailed theory of operation for the VHF circuits in the radio. Details of the theory of operation and trouble shooting for the the associated Controller circuits are included in this Section of the manual. 2.0 VHF (146-174MHz) Receiver 2.1 Receiver Front-End The received signal is applied to the radio’s antenna input connector and routed through the harmonic filter and antenna switch. The insertion loss of the harmonic filter/antenna switch is less than 1 dB. The signal is routed to the first filter (4-pole), which has an insertion loss of 2 dB typically. The output of the filter is matched to the base of the LNA (Q303) that provides a 16 dB gain and a noise figure of better than 2 dB. Current source Q301 is used to maintain the collector current of Q303. Diode CR301 protects Q303 by clamping excessive input signals. Q303 output is applied to the second filter (3-pole) which has an insertion loss of 1.5 dB. In Distance mode, Q304 turns on and causes D305 to conduct, thus bypassing C322 and R337. In Local mode, the signal is routed through C322 and R337, thus inserting 7 dB attenuation. Since the attenuator is located after the RF amplifier, the receiver sensitivity is reduced only by 6 dB, while the overall third order input intercept is raised. The first mixer is a passive, double-balanced type, consisting of T300, T301 and U302. This mixer provides all of the necessary rejection of the half-IF spurious response. High-side injection at +15 dBm is delivered to the first mixer. The mixer output is then connected to a duplex network which matches its output to the XTAL filter input (FL300) at the IF frequency of 44.85 MHz. The duplex network terminates into a 50 ohm resistor (R340) at all other frequencies. Antenna Front Filter 12.5kHzFilter LNA Second Filter Mixer 4- Pole Xtal Filter IF Amp 25kHzFilter First LO 25kHzFilter IFIC 2nd LO Xtal Osc Phase Shift Element Controller Figure 2-1 VHF Receiver Block Diagram 2-2 THEORY OF OPERATION 2.2 Receiver Back End The IF signal from the crystal filter enters the IF amplifier which provides 20 dB of gain and feeds the IF IC at pin 1. The first IF signal at 44.85 MHz mixes with the second local oscillator (LO) at 44.395 MHz to produce the second IF at 455 kHz. The second LO uses the external crystal Y301. The second IF signal is amplified and filtered by two external ceramic filters (FL303/FL302 for 12.5KHz channel spacing and FL304/FL301 for 25KHz channel spacing). The IF IC demodulates the signal by means of a quadrature detector and feeds the detected audio (via pin 7) to the audio processing circuits. At IF IC pin 5, an RSSI signal is available with a dynamic range of 70 dB. 3.0 VHF Transmitter Power Amplifier (146-174 MHz) The radio’s 25W PA is a three-stage amplifier used to amplify the output from the TX_INJ to the antenna port. All three stages utilize LDMOS technology. The gain of the first stage (U101)and the second stage (Q105) is adjustable and is controlled by pin 7 of U103-2 via U103-3 and U102-1. It is followed by an LDMOS final stage Q100. Pin Diode Antenna Switch From VCO (TX_INJ) Controlled Stage PA Driver PA-Final Stage Antenna Harmonic Filter RF Jack Coupler Bias Forward A S FI C _C M P SPI BUS PA PWR SET L oo p C ont r ol le r U 103 - 2 Temperature Sense Figure 2-2 VHF Transmitter Block Diagram Devices U101, Q105 and Q100 are surface mounted. A metal clip ensures good thermal contact between both the driver and final stage, and the chassis. 3.1 First Power Controller Stage The first stage (U101) is a 20dB gain integrated circuit containing two LDMOS FET amplifier stages. It amplifies the RF signal from the VCO (TX_INJ). The output power of stage U101 is controlled by a DC voltage applied to pin 1 from the op-amp U103-3, pin 8. The control voltage simultaneously varies the bias of two FET stages within U101. This biasing point determines the overall gain of U101 and therefore its output drive level to Q105, which in turn controls the output power of the PA. VHF Transmitter Power Amplifier (146-174 MHz) 2-3 Op-amp U103-3 monitors the drain current of U101 via resistor R122 and adjusts the bias voltage of U101. In receive mode, the DC voltage from RX_EN line turns on Q101, which in turn switches off the biasing voltage to U101. 3.2 Power Controlled Driver Stage The next stage is an LDMOS device (Q105) which provides a gain of 12dB. This device requires a positive gate bias and a quiescent current flow for proper operation. The bias is set during transmit mode by the drain current control op-amp U102-1, and fed to the gate of Q105 via the resistive network. Op-amp U102-1 monitors the drain current of Q105 via resistors R126-7 and adjusts the bias voltage of Q105 so that the current remains constant. In receive mode the DC voltage from RX_EN line turns on Q102, which in turn switches off the biasing voltage to Q105. 3.3 Final Stage The final stage is an LDMOS device (Q100) providing a gain of 12dB. This device also requires a positive gate bias and a quiescent current flow for proper operation. The voltage of the line PA_BIAS is set in transmit mode by the ASFIC and fed to the gate of Q100 via the resistive network R134, R131. This bias voltage is tuned in the factory. If the transistor is replaced, the bias voltage must be tuned using the Tuner. Care must be taken not to damage the device by exceeding the maximum allowed bias voltage. The device’s drain current is drawn directly from the radio’s DC supply voltage input, B+, via L117 and L115. A matching network consisting of C1004-5, C1008-9, C1021, C1013, C1019, L116: and two striplines, transforms the impedance to 50 ohms and feeds the directional coupler. 3.4 Bi-Directional Coupler The bi-directional Coupler is a microstrip printed circuit, which couples a small amount of the forward and reverse power of the RF power from Q100.The coupled signal is rectified to an output power which is proportional to the DC voltage rectified by diode D105; and the resulting DC voltage is routed to the power control section to ensure that the forward power out of the radio is held to a constant value. 3.5 Antenna Switch The antenna switch utilizes the existing dc feed (B+) to the last stage device (Q100). The basic operation is to have both PIN diodes (D103, D104) turned on during key-up by forward biasing them. This is achieved by pulling down the voltage at the cathode end of D104 to around 12.4V (0.7V drop across each diode). The current through the diodes needs to be set around 100 mA to fully open the transmit path through resistor R108. Q106 is a current source controlled by Q103 which is turned on in Tx mode by TX_EN. VR102 ensures that the voltage at resistor R107 never exceeds 5.6V. 2-4 3.6 THEORY OF OPERATION Harmonic Filter Inductors L111, L112 and L113 along with capacitors C1011, C1024, C1025, C1022, C1020, C1016, C1017 and C1026 form a low-pass filter to attenuate harmonic energy coming from the transmitter. Resistor R150 along with L126 drains any electrostatic charges that might otherwise build up on the antenna. The harmonic filter also prevents high level RF signals above the receiver passband from reaching the receiver circuits to improve spurious response rejection. 3.7 Power Control The output power is regulated by using a forward power detection control loop. A directional coupler samples a portion of the forward and reflected RF power. The forward sampled RF is rectified by diode D105, and the resulting DC voltage is routed to the operational amplifier U100. The error output current is then routed to an integrator, and converted into the control voltage. This voltage controls the bias of the pre-driver (U101) and driver (Q105) stages. The output power level is set by way of a DAC, PWR_SET, in the audio processing IC (U504), which acts at the forward power control loop reference. The sampled reflected power is rectified by diode D107,The resulting DC voltage is amplified by an operational amplifier U100 and routed to the summing junction. This detector protects the final stage Q100 from reflected power by increasing the error current. The temperature sensor protects the final stage Q100 from overheating by increasing the error current. A thermistor RT100 measures the final stage Q100 temperature. The voltage divider output is routed to an operational amplifier U103 and then goes to the summing junction. The Zener Diode VR101 keeps the loop control voltage below 5.6V and eliminates the DC current from the 9.3 regulator U501. Two local loops for the Pre Driver (U101) and for the Driver (Q105) are used in order to stabilize the current for each stage. In Rx mode, the two transistors Q101 and Q102 go to saturation and shut down the transmitter by applying ground to the Pre Driver U101 and for the Driver Q105 control. 4.0 VHF (146-174MHz) Frequency Synthesis The synthesizer consists of a reference oscillator (Y201), low voltage Fractional-N (LVFRAC-N) synthesizer (U200), and a voltage controlled oscillator (VCO) (U201). 4.1 Reference Oscillator The reference oscillator is a crystal (Y201) controlled Colpitts oscillator and has a frequency of 16.8MHz. The oscillator transistor and start-up circuit are located in the LVFRAC-N (U200) while the oscillator feedback capacitors, crystal, and tuning varactors are external. An analog-to-digital (A/D) converter internal to the LVFRAC-N (U200) and controlled by the microprocessor via SPI sets the voltage at the warp output of U200 pin 25. This sets the frequency of the oscillator. Consequently, the output of the crystal Y201 is applied to U200 pin 23. The method of temperature compensation is to apply an inverse Bechmann voltage curve, which matches the crystal’s Bechmann curve to a varactor that constantly shifts the oscillator back on frequency. The crystal vendor characterizes the crystal over a specified temperature range and codes this information into a bar code that is printed on the crystal package. In production, this crystal code is read via a 2-dimensional bar code reader and the parameters are saved. VHF (146-174MHz) Frequency Synthesis 2-5 This oscillator is temperature compensated to an accuracy of +/-2.5 PPM from -30 to 60 degrees C. The temperature compensation scheme is implemented by an algorithm that uses five crystal parameters (four characterize the inverse Bechmann voltage curve and one for frequency accuracy of the reference oscillator at 25 degrees C). This algorithm is implemented by the LVFRAC-N (U200) at the power up of the radio. TCXO Y200, along with its corresponding circuitry R204, R205, R210, and C2053, are not placed as the temperature compensated crystal proved to be reliable. 4.2 Fractional-N Synthesizer The LVFRAC-N U200 consists of a pre-scaler, programmable loop divider, control divider logic, phase detector, charge pump, A/D converter for low frequency digital modulation, balanced attenuator used to balance the high and low frequency analog modulation, 13V positive voltage multiplier, serial interface for control, and a super filter for the regulated 5 volts. DATA (U403 PIN 100) CLOCK (U403 PIN 1) CSX (U403 PIN 2) MOD IN (U501 PIN 40) +5V (U503 PIN 1) +5V (U503 PIN 1) 7 8 9 10 13, 30 5, 20, 34, 36 REFERENCE OSCILLATOR 23 24 VOLTAGE MULTIPLIER FREFOUT CLK GND CEX MODIN VCC, DC5V IOUT IADAPT VDD, DC5V MODOUT XTAL1 U200 XTAL2 FRACTIONAL-N SYNTHESIZER 25 WARP 32 PREIN 47 LOCK DATA LOW VOLTAGE VCP VMULT2 14 15 48 43 45 LOOP FILTER STEERING LINE 41 AUX3 2 AUX1 BIAS2 FREF (U504 PIN 34) 6, 22, 33, 44 3 1 BIAS1 LOCK (U403 PIN 56) 19 AUX4 AUX2 SFOUT VMULT1 4 VCO Bias LO RF INJECTION TRB VOLTAGE 28 FILTERED 5V CONTROLLED OSCILLATOR 40 TX RF INJECTION (1ST STAGE OF PA) 39 BWSELECT To IF Section PRESCALER IN Figure 2-3 VHF Synthesizer Block Diagram A voltage of 5V applied to the super filter input (U200, pin 30) supplies an output voltage of 4.5Vdc (VSF) at U200, pin 28. This supplies 4.5 V to the VCO Buffer IC U201. To generate a high voltage to supply the phase detector (charge pump) output stage at pin VCP (U200, pin 47) while using a low voltage 3.3Vdc supply, a 13V positive voltage multiplier is used (D200, D201, and capacitors C2024, 2025, 2026, 2055, 2027, 2001). Output lock (U200, pin 4) provides information about the lock status of the synthesizer loop. A high level at this output indicates a stable loop. A 16.8 MHz reference frequency is provided at U200, pin 19. 2-6 THEORY OF OPERATION 4.3 Voltage Controlled Oscillator (VCO) The Voltage Controlled Oscillator (VCO) consists of the VCO/Buffer IC (VCOBIC, U201), the TX and RX tank circuits, the external RX amplifier, and the modulation circuitry. AUX3 (U200 Pin 2) Prescaler Out TRB IN Pin 20 Rx-SW Pin7 Tx-SW Pin13 (U200 Pin 28) Pin 19 U200 Pin 32 Pin 12 TX/RX/BS Switching Network Vcc-Superfilter Pin3 LO RF INJECTION Presc U201 VCOBIC Q200 Buffer Low Pass Filter Collector/RF in Steer Line Voltage (VCTRL) Pin4 RX Tank RX VCO Circuit TX VCO Circuit Rx Active Bias Pin5 Pin6 TX Tank RX RX Pin8 Pin14 TX Tx Active Bias Pin16 Pin15 TX Pin10 Vcc-Logic TX RF Injection Attenuator Vsens Circuit Pin18 (U200 Pin28) VCC Buffers Pin2 Pin1 Rx-I adjust Tx-I adjust Pins 9,11,17 (U200 Pin 28) Figure 2-4 VHF VCO Block Diagram The VCOBIC together with the LVFRAC-N (U200) generate the required frequencies in both transmit and receive modes. The TRB line (U201, pin 19) determines which VCO and buffer is enabled (high being TX output at pin 10, low being RX output at pin 8). A sample of the signal from the enabled output is routed from U201, pin 12 (PRESC_OUT), via a low pass filter to U200, pin 32 (PREIN). A steering line voltage between 3.0V and 10.0V at varactor D204 tunes the TX VCO through the frequency range of 146-174MHz, and at D203 tunes the RX VCO through the frequency range of 190-219MHz. The external RX amplifier is used to increase the output from U201, pin 9 from 3-4 dBm to the required 15dBm for proper mixer operation. In TX mode, the modulation signal from the LVFRAC-N (U200, pin 41) is applied to the VCO by way of the modulation circuit D205, R212, R211, C2073. VHF (146-174MHz) Frequency Synthesis 4.4 2-7 Synthesizer Operation The synthesizer consists of a low voltage FRAC-N IC (LVFRAC-N), reference oscillator, charge pump circuits, loop filter circuit, and DC supply. The output signal (PRESC_OUT) of the VCOBIC (U201, pin 12) is fed to the PREIN, pin 32 of U200 via a low pass filter which attenuates harmonics and provides a correct input level to the LVFRAC-N in order to close the synthesizer loop. The pre-scaler in the synthesizer (U200) is a dual modulus pre-scaler with selectable divider ratios. The divider ratio of the pre-scaler is controlled by the loop divider, which in turn receives its inputs via the SPI. The output of the pre-scaler is applied to the loop divider. The output of the loop divider is connected to the phase detector, which compares the loop divider’s output signal with the reference signal. The reference signal is generated by dividing down the signal of the reference oscillator (Y201). The output signal of the phase detector is a pulsed dc signal that is routed to the charge pump. The charge pump outputs a current from U200, pin 43 (IOUT). The loop filter (consisting of R224, R217, R234, C2074, C2075, C2077, C2078, C2079, C2080, C2028, and L205) transforms this current into a voltage that is applied the varactor diodes D203 and D204 for RX and TX respectively. The output frequency is determined by this control voltage. The current can be set to a value fixed in the LVFRAC-N or to a value determined by the currents flowing into BIAS 1 (U200, pin 40) or BIAS 2 (U200, pin 39). The currents are set by the value of R200 or R206 respectively. The selection of the three different bias sources is done by software programming. To modulate the synthesizer loop, a two-spot modulation method is utilized via the MODIN (U200, pin 10) input of the LVFRAC-N. The audio signal is applied to both the A/D converter (low frequency path) and the balance attenuator (high frequency path). The A/D converter converts the low frequency analog modulating signal into a digital code which is applied to the loop divider, thereby causing the carrier to deviate. The balance attenuator is used to adjust the VCO’s deviation sensitivity to high frequency modulating signals. The output of the balance attenuator is presented at the MODOUT port of the LVFRAC-N (U200,pin 41) and connected to the VCO modulation varactor D205. 2-8 5.0 THEORY OF OPERATION Controller Theory of Operation This section provides a detailed theory of operation for the radio and its components. The main radio is a single-board design, consisting of the transmitter, receiver, and controller circuits. A control head is connected by an extension cable. The control head contains LED indicators, a microphone connector, buttons, and speaker. In addition to the power cable and antenna cable, an accessory cable can be attached to a connector on the rear of the radio. The accessory cable enables you to connect accessories to the radio, such as an external speaker, emergency switch, foot-operated PTT, and ignition sensing, etc. External Microphone To Synthesizer Mod Out 16.8 MHz Reference Clock from Synthesizer Audio/Signaling Architecture Disc Audio ASFIC_CMP . Internal Microphone External Speaker Audio PA Internal Speaker µP Clock SPI To RF Section Digital Architecture SCI to Accessory & Control Head Connector RAM EEPROM 3.3V Regulator HC11FL0 FLASH Figure 2-5 Controller Block Diagram 5.1 Radio Power Distribution Voltage distribution is provided by five separate devices: ■ U514 P-cH FET - Batt + (Ext_SWB+) ■ U501 LM2941T - 9.3V ■ U503 LP2951CM - 5V ■ U508 MC 33269DTRK - 3.3V ■ U510 LP2986ILDX - 3.3V Digital Handset Controller Theory of Operation 2-9 The DC voltage applied to connector P2 supplies power directly to the following circuitry: ■ Electronic on/off control ■ RF power amplifier ■ 12 volts P-cH FET -U514 ■ 9.3 volt regulator ■ Audio PA Ignition Auto On/Off Switch Control B+ Control Head RF_PA Audio_PA Mic Connector Ferrite Bit Filt_B+ Antenna Switch Power Control 500mA FET P-CH On/Off Control SW_Filt_B+ 11-16.6V 0.9A Status LEDs 7_Seg 7_Seg DOT Bed to 7-Seg Back light Shift Reg Acces Conn Audio PA_Soutdown Power Loop Op_Amp 9.3V 65mA U501 9.3V Regulator Keypad Mic Bias 9V, 5mA 0.85A Reset 9.3V 45mA On/Off Control U503 5V RF Regulator 500mA Rx_Amp PA_Pre-driver PA Driver 3.2V 72mA 45mA LVFRAC_N IF_Amp 9.3V 75mA 9.3V 162mA U508 3.3V RF Reg 50mA 25mA ASFIC_CMP IFIC RX Cct U510 3.3V D Reg 90mA micro P RAM Flash EEPROM Figure 2-6 DC Power Distribution Block Diagram Regulator U501 is used to generate the 9.3 volts required by some audio circuits, the RF circuitry and power control circuitry. Input and output capacitors are used to reduce high frequency noise. Resistors R5001 / R5081 set the output voltage of the regulator. This regulator output is electronically enabled by a 0 volt signal on pin 2. Q502, Q505 and R5038 are used to disable the regulator when the radio is turned off. Voltage regulator U510 provides 3.3 volts for the digital circuitry. Operating voltage is from the regulated 9.3V supply. Input and output capacitors are used to reduce high frequency noise and provide proper operation during battery transients. U510 provides a reset output that goes to 0 volts if the regulator output goes below 3.1 volts. This is used to reset the controller to prevent improper operation. Voltage regulator U508 provides 3.3V for the RF circuits and ASFIC_CMP. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. 2-10 THEORY OF OPERATION Voltage regulator U503 provides 5V for the RF circuits. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. VSTBY is used only for CM360 5-tone radios. The voltage VSTBY, which is derived directly from the supply voltage by components R5103 and VR502, is used to buffer the internal RAM. Capacitor C5120 allows the battery voltage to be disconnected for a couple of seconds without losing RAM parameters. Dual diode D501 prevents radio circuitry from discharging this capacitor. When the supply voltage is applied to the radio, C5120 is charged via R5103 and D501. 5.2 Protection Devices Diode VR500 acts as protection against ESD, wrong polarity of the supply voltage, and load dump. VR692 - VR699 are for ESD protection. 5.3 Automatic On/Off The radio can be switched ON in any one of the following three ways: 5.3.1 ■ On/Off switch. (No Ignition Mode) ■ Ignition and On/Off switch (Ignition Mode) ■ Emergency No Ignition Mode When the radio is connected to the car battery for the first time, Q500 will be in saturation, Q503 will cut-off, Filt_B+ will pass through R5073, D500, and S5010-pin 6 (On/Off switch). When S5010 is ON, Filt_B+ will pass through S5010-pin5, D511, R5069, R5037 and base of Q505 and move Q505 into saturation. This pulls U501-pin2 through R5038, D502 to 0.2V and turns On U514 and U501 9.3V regulator which supplies voltage to all other regulators and consequently turns the radio on, When U504 (ASFIC_CMP) gets 3.3V, GCB2 goes to 3.3V and holds Q505 in saturation, for soft turn off. 5.3.2 Ignition Mode When ignition is connected for the first time, it will force high current through Q500 collector, This will move Q500 out of saturation and consequently Q503 will cut-off. S5010 pin 6 will get ignition voltage through R601 (for load dump), R610, (R610 & C678 are for ESD protection), VR501, R5074, and D500. When S5010 is ON, Filt_B+ passes through S5010-pin 5, D511, R5069, R5037 and base of Q505 and inserts Q505 into saturation. This pulls U501-pin 2 through R5038, D502 to 0.2V and turns on U514 and U501 9.3V regulator which supply voltage to all other regulators and turns the radio on, When U504 (ASFIC_CMP) get 3.3V supply, GCB2 goes to 3.3V and holds Q505 in saturation state to allow soft turn off, When ignition is off Q500, Q503 will stay at the same state so S5010 pin 6 will get 0V from Ignition, Q504 goes from Sat to Cut, ONOFF_SENSE goes to 3.3V and it indicates to the radio to soft turn itself by changing GCB2 to ‘0’ after de registration if necessary. Controller Theory of Operation 5.3.3 2-11 Emergency Mode The emergency switch (P1 pin 9), when engaged, grounds the base of Q506 via EMERGENCY _ACCES_CONN. This switches Q506 to off and consequently resistor R5020 pulls the collector of Q506 and the base of Q506 to levels above 2 volts. Transistor Q502 switches on and pulls U501 pin2 to ground level, thus turning ON the radio. When the emergency switch is released R5030 pulls the base of Q506 up to 0.6 volts. This causes the collector of transistor Q506 to go low (0.2V), thereby switching Q502 to off. While the radio is switched on, the µP monitors the voltage at the emergency input on the accessory connector via U403-pin 62. Three different conditions are distinguished: no emergency kit is connected, emergency kit connected (unpressed), and emergency press. If no emergency switch is connected or the connection to the emergency switch is broken, the resistive divider R5030 / R5049 will set the voltage to about 3.14 volts (indicates no emergency kit found via EMERGENCY_SENSE line). If an emergency switch is connected, a resistor to ground within the emergency switch will reduce the voltage on EMERGENCY _SENSE line, and indicate to the µP that the emergency switch is operational. An engaged emergency switch pulls line EMERGENCY _SENSE line to ground level. Diode VR503 limits the voltage to protect the µP input. While EMERGENCY _ACCES_CONN is low, the µP starts execution, reads that the emergency input is active through the voltage level of µP pin 64, and sets the DC POWER ON output of the ASFIC CMP pin 13 to a logic high. This high will keep Q505 in saturation for soft turn off. 5.4 Microprocessor Clock Synthesiser The clock source for the µP system is generated by the ASFIC CMP (U504). Upon power-up the synthesizer IC (FRAC-N) generates a 16.8 MHz waveform that is routed from the RF section to the ASFIC CMP pin 34. For the main board controller the ASFIC CMP uses 16.8 MHz as a reference input clock signal for its internal synthesizer. The ASFIC CMP, in addition to audio circuitry, has a programmable synthesizer which can generate a synthesized signal ranging from 1200Hz to 32.769MHz in 1200Hz steps. When power is first applied, the ASFIC CMP will generate its default 3.6864MHz CMOS square wave UP CLK (on U504 pin 28) and this is routed to the µP (U403 pin 90). After the µP starts operation, it reprograms the ASFIC CMP clock synthesizer to a higher UP CLK frequency (usually 7.3728 or 14.7456 MHz) and continues operation. The ASFIC CMP may be reprogrammed to change the clock synthesizer frequencies at various times depending on the software features that are executing. In addition, the clock frequency of the synthesizer is changed in small amounts if there is a possibility of harmonics of the clock source interfering with the desired radio receive frequency. The ASFIC CMP synthesizer loop uses C5025, C5024 and R5033 to set the switching time and jitter of the clock output. If the synthesizer cannot generate the required clock frequency it will switch back to its default 3.6864MHz output. Because the ASFIC CMP synthesizer and the µP system will not operate without the 16.8 MHz reference clock it (and the voltage regulators) should be checked first when debugging the system. 2-12 5.5 THEORY OF OPERATION Serial Peripheral Interface (SPI) The µP communicates to many of the IC’s through its SPI port. This port consists of SPI TRANSMIT DATA (MOSI) (U403-pin100), SPI RECEIVE DATA (MISO) (U403-pin 99), SPI CLK (U0403-pin1) and chip select lines going to the various IC’s, connected on the SPI PORT (BUS). This BUS is a synchronous bus, in that the timing clock signal CLK is sent while SPI data (SPI TRANSMIT DATA or SPI RECEIVE DATA) is sent. Therefore, whenever there is activity on either SPI TRANSMIT DATA or SPI RECEIVE DATA there should be a uniform signal on CLK. The SPI TRANSMIT DATA is used to send serial from a µP to a device, and SPI RECEIVE DATA is used to send data from a device to a µP. There are two IC’s on the SPI BUS, ASFIC CMP (U504 pin 22)), and EEPROM (U400). In the RF sections there is one IC on the SPI BUS, the FRAC-N Synthesizer. The chip select line CSX from U403 pin 2 is shared by the ASFIC CMP and FRAC-N Synthesizer. Each of these IC’s check the SPI data and when the sent address information matches the IC’s address, the following data is processed. When the µP needs to program any of these Is it brings the chip select line CSX to a logic “0” and then sends the proper data and clock signals. The amount of data sent to the various IC’s are different; e.g., the ASFIC CMP can receive up to 19 bytes (152 bits). After the data has been sent the chip select line is returned to logic “1”. 5.6 SBEP Serial Interface The SBEP serial interface allows the radio to communicate with the Customer Programming Software (CPS), or the Universal Tuner via the Radio Interface Box (RIB) or the cable with internal RIB. This interface connects to the SCI pin via control head connector (J2-pin 17) and to the accessory connector P1-6 and comprises BUS+. The line is bi-directional, meaning that either the radio or the RIB can drive the line. The µP sends serial data and it reads serial data via pin 97. Whenever the µP detects activity on the BUS+ line, it starts communication. 5.7 General Purpose Input/Output The controller provides six general purpose lines (PROG I/O) available on the accessory connector P1 to interface to external options. Lines PROG IN 3 and 6 are inputs, PROG OUT 4 is an output and PROG IN OUT 8, 12 and 14 are bi-directional. The software and the hardware configuration of the radio model define the function of each port. ■ PROG IN 3 can be used as external PTT input, or others, set by the CPS. The µP reads this port via pin 72 and Q412. ■ PROG OUT 4 can be used as external alarm output, set by the CPS. Transistor Q401 is controlled by the µP (U403 pin 55) ■ PROG IN 6 can be used as normal input, set by the CPS. The µP reads this port via pin 73 and Q411. This pin is also used to communicate with the RIB if resistor R421 is placed. ■ DIG IN OUT 8,12,14 are bi-directional and use the same circuit configuration. Each port uses an output Q416, Q404, Q405 controlled by µP pins 52, 53, 54. The input ports are read through µP pins 74, 76, 77; using Q409, Q410, Q411 Controller Theory of Operation 5.8 2-13 Normal Microprocessor Operation For this radio, the µP is configured to operate in one of two modes, expanded and bootstrap. In expanded mode the µP uses external memory devices to operate, whereas in bootstrap operation the µP uses only its internal memory. In normal operation of the radio the µP is operating in expanded mode as described below. During normal operation, the µP (U403) is operating in expanded mode and has access to 3 external memory devices; U400 (EEPROM), U402 (SRAM), U404 (Flash). Also, within the µP there are 3 Kilobytes of internal RAM, as well as logic to select external memory devices. The external EEPROM (U400) space contains the information in the radio which is customer specific, referred to as the codeplug. This information consists of items such as: 1) what band the radio operates in, 2) what frequencies are assigned to what channel, and 3) tuning information. The external SRAM (U402) as well as the µP’s own internal RAM space are used for temporary calculations required by the software during execution. All of the data stored in both of these locations is lost when the radio powers off. The µP provides an address bus of 16 address lines (ADDR 0 - ADDR 15), and a data bus of 8 data lines (DATA 0 - DATA 7). There are also 3 control lines; CSPROG (U403-38) to chip select U404-pin 30 (FLASH), CSGP2 (U403-pin 41) to chip select U404-pin 20 (SRAM) and PG7_R_W (U403-pin 4) to select whether to read or to write. The external EEPROM (U400-pin1). When the µP is functioning normally, the address and data lines should be toggling at CMOS logic levels. Specifically, the logic high levels should be between 3.1 and 3.3V, and the logic low levels should be between 0 and 0.2V. No other intermediate levels should be observed, and the rise and fall times should be <30ns. The low-order address lines (ADDR 0 - ADDR 7) and the data lines (DATA 0-DATA 7) should be toggling at a high rate, e.g., you should set your oscilloscope sweep to 1us/div. or faster to observe individual pulses. High speed CMOS transitions should also be observed on the µP control lines. On the µP the lines XIRQ (U403-pin 48), MODA LIR (U403-pin 58), MODB VSTPY (U403-pin 57) and RESET (U403-pin 94) should be high at all times during normal operation. Whenever a data or address line becomes open or shorted to an adjacent line, a common symptom is that the RESET line goes low periodically, with the period being in the order of 20ms. In the case of shorted lines you may also detect the line periodically at an intermediate level, i.e. around 2.5V when two shorted lines attempt to drive to opposite rails. The MODA LIR (U403-pin 58) and MODB VSTPY (U403-pin 57) inputs to the µP must be at a logic “1” for it to start executing correctly. After the µP starts execution it will periodically pulse these lines to determine the desired operating mode. While the Central Processing Unit (CPU) is running, MODA LIR is an open-drain CMOS output which goes low whenever the µP begins a new instruction. An instruction typically requires 2-4 external bus cycles, or memory fetches. There are eight analog-to-digital coverter ports (A/D) on U403 labelled within the device block as PEO-PE7. These lines sense the voltage level ranging from 0 to 3.3V of the input line and convert that level to a number ranging from 0 to 255 which is read by the software to take appropriate action. 2-14 5.9 THEORY OF OPERATION Static Random Access Memory (SRAM) The SRAM (U402) contains temporary radio calculations or parameters that can change very frequently, and which are generated and stored by the software during its normal operation. The information is lost when the radio is turned off. The device allows an unlimited number of write cycles. SRAM accesses are indicated by the CS signal U402 (which comes from U403-CSGP2) going low. U402 is commonly referred to as the external RAM as opposed to the internal RAM which is the 3 Kilobytes of RAM which is part of the 68HC11FL0. Both RAM spaces serve the purpose. However, the internal RAM is used for the calculated values which are accessed most often. Capacitor C402 and C411 serves to filter out any AC noise which may ride on +3.3 V at U402 6.0 Control Board Audio and Signalling Circuits 6.1 Audio Signalling Filter IC and Compander (ASFIC CMP) The ASFIC CMP (U504) used in the controller has the following four functions: 1. RX/TX audio shaping, i.e. filtering, amplification, attenuation 2. RX/TX signaling, PL/DPL/HST/MDC 3. Squelch detection 4. µP clock signal generation The ASFIC CMP is programmable through the SPI BUS (U504 pins-20/21/22), normally receiving 19 bytes. This programming sets up various paths within the ASFIC CMP to route audio and/or signaling signals through the appropriate filtering, gain and attenuator blocks. The ASFIC CMP also has 6 General Control Bits GCB0-5 which are CMOS level outputs and used for the following: ■ GCBO - BW Select ■ GCBI - switches the audio PA On/Off ■ GCB2 - DC Power On switches the voltage regulator (and the radio) on and off ■ GCB3 - Control on MUX U509 pin 9 to select between Low Cost Mic path to STD Mic Path ■ GCB4 - Control on MUX U509 pin 11 to select between Flat RX path to filtered RX path on the accessory connector. ■ GCB5 - Control on MUX U509 pin 10 to select between Flat TX path mute and Flat TX path Transmit Audio Circuits 7.0 2-15 Transmit Audio Circuits J2 24kOhms U509 15 MIC 46 35 P1 48 2 FLAT TX AUDIO MIC INT GCB3 MIC EXT U509 5 36 TX RTN MUX CONTROL HEAD CONNECTOR EXT MIC 44 TX SND 42 MUX AUX TX ACCESSORY CONNECTOR FILTERS AND PREEMPHASIS MIC ASFIC_CMP IN U504 LIMITER HS SUMMER SPLATTER FILTER LS SUMMER 38 GCB5 FLAT TX AUDIO MUTE VCO ATN ATTENUATOR MOD IN 40 TO RF SECTION (SYNTHESIZER) Figure 2-7 Transmit Audio Paths 7.1 Microphone Input Path The radio supports 2 distinct microphone paths known as internal (from control head J2-15) and external mic (from accessory connector P1-2) and an auxiliary path (FLAT TX AUDIO, from accessory connector P1-5). The microphones used for the radio require a DC biasing voltage provided by a resistive network. The two microphone audio input paths enter the ASFIC CMP at U504-pin 48 (external mic) and U504-pin 46 (internal mic). The microphone is plugged into the radio control head and connected to the audio DC via J2-pin 15. The signal is then routed via C5045 to MUX U509 that select between two paths with different gain to support Low Cost Mic (Mic with out amplifier in it) and Standard Mic. 7.1.1 Low Cost Microphone Hook Pin is shorted to Pin 1(9.3V) inside the Low Cost Mic, This routes 9.3V to R429, and creates 2.6V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 = ‘0’. The audio signal is routed from C5045 via U509-5 (Z0), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int. mic (C5046 100nF creates a159Hz pole with U504- 46 int mic impedance of 16Kohm). 2-16 7.1.2 THEORY OF OPERATION Standard Microphone Hook Pin is shorted to the hook mic inside the standard Mic, If the mic is out off hook, 3.3V is routed to R429 via R458, D401, and it create 0.7V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 =‘1’. The audio signal is routed from C5045 via U509-3 (Z1), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int mic (C5046 100nF create a159Hz pole with U504- 46 int mic impedance of 16Kohm). 9.3VDC is routed via R5077, R5075 to J2-15, It create 4.65V with Mic Impedance. C5010 supplies AC Ground to create AC impedance of 510 Ohms via R5075. and Filter 9.3V DC mic bias supply. Note: The audio signal at U504-pin 46 should be approximately 12mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The external microphone signal enters the radio on accessory connector P1 pin 2 and is routed via line EXT MIC to R5054. R5078 and R5076 provide the 9.3Vdc bias. Resistive divider R5054/ R5070 divide the input signal by 5.5 and provide input protection for the CMOS amplifier input. R5076 and C5009 provide a 510 ohm AC path to ground that sets the input impedance for the microphone and determines the gain based on the emitter resistor in the microphone’s amplifier circuit. C5047 serves as a DC blocking capacitor. The audio signal at U504-pin 48 should be approximately 14mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The FLAT TX AUDIO signal from accessory connector P1-pin 5 is fed to the ASFIC CMP (U504 pin 42 through U509 pin 2 to U509 pin 15 via U506 OP-AMP circuit and C5057. The ASFIC has an internal AGC that can control the gain in the mic audio path. The AGC can be disabled / enabled by the µP. Another feature that can be enabled or disabled in the ASFIC is the VOX. This circuit, along with Capacitor C5023 at U504-pin 7, provides a DC voltage that can allow the µP to detect microphone audio. The ASFIC can also be programmed to route the microphone audio to the speaker for public address operation. 7.2 PTT Sensing and TX Audio Processing Internal microphone PTT is sensed by µP U403 pin 71. Radio transmits when this pin is “0” and selects inside the ASFIC_ CMP U504 internal Mic path. When the internal Mic PTT is “0” then external Mic PTT is grounded via D402. External Mic PTT is sensed by U403 pin 72 via Q412 circuits. The radio transmits when this pin is “0” and selects inside the ASFIC _CMP U504 External Mic path. Inside the ASFIC CMP, the mic audio is filtered to eliminate frequency components outside the 3003000Hz voice band, and pre-emphasized if pre-emphasis is enabled. The signal is then limited to prevent the transmitter from over deviating. The limited mic audio is then routed through a summer, which is used to add in signaling data, and then to a splatter filter to eliminate high frequency spectral components that could be generated by the limiter. The audio is then routed to an attenuator, which is tuned in the factory or the field to set the proper amount of FM deviation. The TX audio emerges from the ASFIC CMP at U504-pin 40 MOD IN, at which point it is routed to the RF section. Transmit Signalling Circuits 8.0 2-17 Transmit Signalling Circuits HS SUMMER 44 MICRO CONTROLLER U403 19 HIGH SPEED CLOCK IN (HSIO) DTMF ENCODER 82 SPI BUS SPLATTER FILTER ASFIC_CMP U504 85 80 5-3-2 STATE ENCODER 18 LOW SPEED CLOCK IN (LSIO) PL ENCODER LS SUMMER ATTENUATOR 40 MOD IN TO RF SECTION (SYNTHESIZER) Figure 2-8 Transmit Signalling Path From a hardware point of view, there are 3 types of signaling: ■ Sub-audible data (PL / DPL / Connect Tone) that gets summed with transmit voice or signaling, ■ DTMF data for telephone communication in trunked and conventional systems, and ■ Audible signaling including MDC and high-speed trunking. Note: All three types are supported by the hardware while the radio software determines which signaling type is available. 8.1 Sub-Audio Data (PL/DPL) Sub-audible data implies signaling whose bandwidth is below 300Hz. PL and DPL waveforms are used for conventional operation and connect tones for trunked voice channel operation. The trunking connect tone is simply a PL tone at a higher deviation level than PL in a conventional system. Although it is referred to as “sub-audible data”, the actual frequency spectrum of these waveforms may be as high as 250 Hz, which is audible to the human ear. However, the radio receiver filters out any audio below 300Hz, so these tones are never heard in the actual system. Only one type of sub-audible data can be generated by U504 (ASFIC CMP) at any one time. The process is as follows, using the SPI BUS, the µP programs the ASFIC CMP to set up the proper lowspeed data deviation and select the PL or DPL filters. The µP then generates a square wave which strobes the ASFIC PL / DPL encode input LSIO U504-pin 18 at twelve times the desired data rate. For example, for a PL frequency of 103Hz, the frequency of the square wave would be 1236Hz. This drives a tone generator inside U504 which generates a staircase approximation to a PL sine wave or DPL data pattern. This internal waveform is then low-pass filtered and summed with voice or data. The resulting summed waveform then appears on U504-pin 40 (MOD IN), where it is sent to the RF board as previously described for transmit audio. A trunking connect tone would be generated in the same manner as a PL tone. 2-18 8.2 THEORY OF OPERATION High Speed Data High speed data refers to the 3600 baud data waveforms, known as Inbound Signaling Words (ISWs) used in a trunking system for high speed communication between the central controller and the radio. To generate an ISW, the µP first programs the ASFIC CMP (U504) to the proper filter and gain settings. It then begins strobing U504-pin 19 (HSIO) with a pulse when the data is supposed to change states. U504’s 5-3-2 State Encoder (which is in a 2-state mode) is then fed to the postlimiter summer block and then the splatter filter. From that point it is routed through the modulation attenuator and then out of the ASFIC CMP to the RF board. MDC is generated in much the same way as trunking ISW. However, in some cases these signals may also pass through a data preemphasis block in the ASFIC CMP. Also these signaling schemes are based on sending a combination of 1200 Hz and 1800 Hz tones only. Microphone audio is muted during high speed data signaling. 8.3 Dual Tone Multiple Frequency (DTMF) Data DTMF data is a dual tone waveform used during phone interconnect operation. It is the same type of tones which are heard when using a “Touch Tone” telephone. There are seven frequencies, with four in the low group (697, 770, 852, 941Hz) and three in the high group (1209, 1336, 1477Hz). The high-group tone is generated by the µP (U403-46) strobing U50419 at six times the tone frequency for tones less than 1440Hz or twice the frequency for tones greater than 1440Hz. The low group tone is generated by the ASFIC CMP, controlled by the µP via SPI bus. Inside U504 the low-group and high-group tones are summed (with the amplitude of the high group tone being approximately 2 dB greater than that of the low group tone) and then preemphasized before being routed to the summer and splatter filter. The DTMF waveform then follows the same path as was described for high-speed data. Receive Audio Circuits 9.0 2-19 Receive Audio Circuits ACCESSORY CONNECTOR 11 1 AUDIO PA U502 9 4 SPKR + 16 SPKR - 1 EXTERNAL SPEAKER 6 INT SPKR+ INT SPKRCONTROL HEAD CONNECTOR 19 MUTE U509 FLT RX AUDIO P1 INTERNAL SPEAKER 20 J2 18 HANDSET AUDIO U505 37 39 10 GCB4 U IO 43 AUX RX 14 41 URX OUT AUDIO GCB1 VOLUME ATTEN. ASFIC_CMP U504 FILTER AND DEEMPHASIS DISC FROM AUDIO RF SECTION (IF IC) 2 DISC PL FILTER LIMITER LIMITER, RECTIFIER FILTER, COMPARATOR LS IO 18 SQUELCH CIRCUIT SQ DET CH ACT 16 17 84 83 MICRO CONTROLLER 80 U403 85 Figure 2-9 Receive Audio Paths 9.1 Squelch Detect The radio’s RF circuits are constantly producing an output at the discriminator (IF IC). This signal (DISC AUDIO) is routed to the ASFIC CMP’s squelch detect circuitry input DISC (U504-pin 2). All of the squelch detect circuitry is contained within the ASFIC CMP. Therefore from a user’s point of view, DISC AUDIO enters the ASFIC CMP, and the ASFIC CMP produces two CMOS logic outputs based on the result. They are CH ACT (U504-16) and SQ DET (U504-17). The squelch signal entering the ASFIC CMP is amplified, filtered, attenuated, and rectified. It is then sent to a comparator to produce an active high signal on CH ACT. A squelch tail circuit is used to produce SQ DET (U504-17) from CH ACT. The state of CH ACT and SQ DET is high (logic “1”) when carrier is detected, otherwise low (logic “0”). CH ACT is routed to the µP pin 84 while SQ DET is routed to the µP pin 83. SQ DET is used to determine all audio mute / unmute decisions except for Conventional Scan. In this case CH ACT is a pre-indicator as it occurs slightly faster than SQ DET. 2-20 9.2 THEORY OF OPERATION Audio Processing and Digital Volume Control The receiver audio signal (DISC AUDIO) enters the controller section from the IF IC where it is.DC coupled to ASFIC CMP via the DISC input U504-pin 2. The signal is then applied to both the audio and the PL/DPL paths The audio path has a programmable amplifier, whose setting is based on the channel bandwidth being received, an LPF filter to remove any frequency components above 3000Hz, and a HPF to strip off any sub-audible data below 300Hz. Next, the recovered audio passes through a deemphasis filter (if it is enabled to compensate for Pre-emphasis which is used to reduce the effects of FM noise). The IC then passes the audio through the 8-bit programmable attenuator whose level is set depending on the value of the volume control. Finally the filtered audio signal passes through an output buffer within the ASFIC CMP. The audio signal exits the ASFIC CMP at AUDIO output (U504 pin 41). The µP programs the attenuator, using the SPI BUS, based on the volume setting. The minimum / maximum settings of the attenuator are set by codeplug parameters. Since sub-audible signaling is summed with voice information on transmit, it must be separated from the voice information before processing. Any sub-audible signaling enters the ASFIC CMP from the IF IC at DISC U504-2. Once inside, it goes through the PL/DPL path. The signal first passes through one of the two low-pass filters, either the PL low-pass filter or the DPL/LST low-pass filter. Either signal is then filtered and goes through a limiter and exits the ASFIC CMP at LSIO (U504-pin 18). At this point, the signal will appear as a square wave version of the sub-audible signal which the radio received. The µP U403 pin 80 will decode the signal directly to determine if it is the tone / code which is currently active on that mode. 9.3 Audio Amplification Speaker (+) Speaker (-) The output of the ASFIC CMP’s digital volume pot, U504-pin 41 is routed through DC blocking capacitor C5049 to the audio PA (U502 pin 1 and 9). The audio power amplifier has one inverted and one non-inverted output that produces the differential audio output SPK+/SPK- (U502 pins 4 and 6) The audio PA is enabled via the ASFIC CMP (U504-GCB1). When the base of Q501 is low, the transistor is off and U502-pin 8 is high, using pull up resistor R5041, and the audio PA is ON. The voltage at U502-pin 8 must be above 8.5Vdc to properly enable the device. If the voltage is between 3.3 and 6.4V, the device will be active but has its input (U502-pins 1/9) off. This is a mute condition which is used to prevent an audio pop when the PA is enabled. The SPK+ and SPK- outputs of the audio PA have a DC bias which varies proportionately with B+ (U502- pin 7). B+ of 11V yields a DC offset of 5V, and B+ of 17V yields a DC offset of 8.5V. If either of these lines is shorted to ground, it is possible that the audio PA will be damaged. SPK+ and SPKare routed to the accessory connector (P1-pin 1 and 16) and to the control head (connector J2-pins 19 and 20). Receive Signalling Circuits 9.4 2-21 Handset Audio Certain handheld accessories have a speaker within them which require a different voltage level than that provided by U502. For these devices HANDSET AUDIO is available at control head connector J2 pin18. The received audio from the output of the ASFIC CMP’s digital volume attenuator is routed to U505 pin 2 where it is amplified. This signal is routed from the output of the op-amp U505 to J2-pin 18. From the control head, the signal is sent directly to the microphone jack. 9.5 Filtered Audio and Flat Audio The ASFIC CMP output audio at U504-pin 39 is filtered and de-emphasized, but has not gone through the digital volume attenuator. From ASFIC CMP U504-pin 39 the signal is routed via R5034 through gate U509-pin 12 and AC coupled to U505-pin 6. The gate controlled by ASFIC CMP port GCB4 selects between the filtered audio signal from the ASFIC CMP pin 39 (URXOUT) or the unfiltered (flat) audio signal from the ASFIC CMP pin 10 (UIO). Resistors R5034 and R5021 determine the gain of op-amp UU505-pin 6 for the filtered audio while R5032 and R5021 determine the gain for the flat Audio. The output of U505-pin 7 is then routed to P1 pin 11 via DC blocking capacitor C5003. Note that any volume adjustment of the signal on this path must be done by the accessory. 10.0 Receive Signalling Circuits DATA FILTER AND DEEMPHASIS DET AUDIO DISCRIMINATOR AUDIO FROM RF SECTION (IF IC) 2 LIMITER HSIO 19 82 44 DISC ASFIC_CMP U504 FILTER LIMITER MICRO CONTROLLER U403 LSIO 18 80 85 PLEAP 8 PLCAP2 25 Figure 2-10 Receive Signalling Paths 10.1 Sub-Audio Data (PL/DPL) and High Speed Data Decoder The ASFIC CMP (U504) is used to filter and limit all received data. The data enters the ASFIC CMP at input DISC (U504 pin 2). Inside U504 the data is filtered according to data type (HS or LS), then it is limited to a 0-3.3V digital level. The MDC and trunking high speed data appear at U504-pin 19, where it connects to the µP U403 pin 80. 2-22 THEORY OF OPERATION The low speed limited data output (PL, DPL, and trunking LS) appears at U504-pin18, where it connects to the µP U403-pin 80. The low speed data is read by the µP at twice the frequency of the sampling waveform; a latch configuration in the ASFIC CMP stores one bit every clock cycle. The external capacitors C5028, and C5026 set the low frequency pole for a zero crossings detector in the limiters for PL and HS data. The hysteresis of these limiters is programmed based on the type of received data. 10.2 Alert Tone Circuits When the software determines that it needs to give the operator an audible feedback (for a good key press, or for a bad key press), or radio status (trunked system busy, phone call, circuit failures), it sends an alert tone to the speaker. It does so by sending SPI BUS data to U504 which sets up the audio path to the speaker for alert tones. The alert tone itself can be generated in one of two ways: internally by the ASFIC CMP, or externally using the µP and the ASFIC CMP. The allowable internal alert tones are 304, 608, 911, and 1823Hz. In this case a code contained within the SPI BUS load to the ASFIC CMP sets up the path and determines the tone frequency, and at what volume level to generate the tone. (It does not have to be related to the voice volume setting.) For external alert tones, the µP can generate any tone within the 100-3000Hz audio band. This is accomplished by the µP generating a square wave which enters the ASFIC CMP at U504 pin 19. Inside the ASFIC CMP this signal is routed to the alert tone generator. The output of the generator is summed into the audio chain just after the RX audio de-emphasis block. Inside U504, the tone is amplified and filtered, then passed through the 8-bit digital volume attenuator, which is typically loaded with a special value for alert tone audio. The tone exits at U504pin 41 and is routed to the audio PA like receive audio. Chapter 3 TROUBLESHOOTING CHARTS This section contains detailed troubleshooting flowcharts. These charts should be used as a guide in determining the problem areas. They are not a substitute for knowledge of circuit operation and astute troubleshooting techniques. It is advisable to refer to the related detailed circuit descriptions in the theory of operation sections prior to troubleshooting a radio. Most troubleshooting charts end up by pointing to an IC to replace. It is not always noted, but it is good practice to verify supplies and grounds to the affected IC and to trace continuity to the malfunctioning signal and related circuitry before replacing any IC. For instance, if a clock signal is not available at a destination, continuity from the source IC should be checked before replacing the source IC. 3-2 1.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2) START Yes Problem in 12 KHz and 25 KHz channel spacing Go to DC Section 9V on Yes R310 (LNA) OK? No Check RX_EN Go to DC Section No 3V to U301 Okay ? Yes Check Q306, Q300 and U403 Check Q304, D305 and U403 Go to SYN Section Go to DC Section No No RX_EN ON ? Yes LOC_DIST ON? Yes Check LOC_DIST Check TPI No LO POWER OK ? Yes Check 5V on R336 No 5V Yes (IF AMP) OK ? Check 3V on R339 Go to A Check D301-304 Replace IF Filters( FL304, FL301) If problem in 25 KHz spacing Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2) 1.1 3-3 Troubleshooting Flow Chart for Receiver (Sheet 2 of 2) From A 3V (IFIC -Vcc) OK ? Go to DC Section No Check the component No Antenna to Mixer circuitry problem No Check visually all receiver components installation ? Yes Installation OK ? Yes Inject - 40dBm (CW) to RF connector Check Power on C332 RF Yes Power > -28 dBM? Check Power on C336 Replace Q305, Q300, U302 Check passive components Replace Q303, Q301 Check passive components No Replace Y301 No Go to DC Section 3V to U301 OK? Yes Y301 OK? No Yes RF Yes Power > -28 dBM? Replace Q302, Y300 Check D301 - 304 Replace U300 Check Y301 44.395 MHz 3-4 2.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 25W Transmitter (Sheet 1 of 3) START No or too low power when keyed Check components between Q100 and RF output, Antenna Switch D104, D103, VR102 and Q106 before replacing Q100 >1.0A Current increase when keyed? >430mA & <1.0A <500mA Check PA Stages Yes >1.5V Control Voltage at TP150 =1.5V? No Check 9.3V Regulator U501 No Voltage U103 pin 5 = 4.7V? Yes Check power settings, tuning & components between U103 Pin 3 and ASFIC Pin 6 before replacing ASFIC No U103 Pin 3 <2.6V Yes Check U103 Yes Short U100 Pin 3 to ground U100 Pin 3 >2Vdc No Check forward Power Sense Circuit Check PA Stages Yes Voltage at TP150 rises? No Check Forward Power Sense Circuit Troubleshooting Flow Chart for 25W Transmitter (Sheet 1 of 3) 2.1 3-5 Troubleshooting Flow Chart for 25W Transmitter (Sheet 2 of 3) Check PA Stages No or too low power when keyed DC Voltage at Q101 & Q102 base=0? Check Q101, R153,R136, R165, R122, R168, R137 No Check U403 Yes No DC Voltage at U103 Pin 10=8.8V <2V Yes DC Voltage at U103 Pin 8 >5V Check resistive network at Pin 9 and 10 of U103 before replacing U101 2-5V Check U103 and Resistive Network at Pin 10 of U103 before replacing U101 Measure DC Voltage at U102 Pin 1 2.3V Pin 1 Voltage at U102 >3V Check Q102, R139, R155, R166, R126, R127, R169, R138, R175, R147 No <2V 2-3V U102 Pin 3 = 8.8V Yes Check U102 before replacing Q105 Check Final PA Stages Check resistance network at pin 1, 2, 3 of U102 before replacing Q105 3-6 2.2 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 25W Transmitter (Sheet 3 of 3) Check Final PA Stage <2V Check Bias Tuning R134, R131, R106 before replacing ASFIC U504 PA_Bias Voltage at R134 2.1V Supply Voltage Replace Q100 2-3V RF Voltage after C1044 >100mV? No Check FGU Yes Voltage across R122 >50mV? No Check components between C1044 & C1117 No Check components between C1117 & Q105 No Check components between Q105 & Q100 Yes RF Voltage Q105 gate >100mV? Yes RF Voltage Q100 gate >1.5V? Yes Check components between Q100 & antenna connector Troubleshooting Flow Chart for Synthesizer 3.0 3-7 Troubleshooting Flow Chart for Synthesizer 5V at U200 pins 5, 20, 34 & 36 Start No Check 5V Regulator U503 Yes No Correct Problem Visual check of the Board OK? Yes Yes 5V at pin 6 of D200 No Yes Is U200 Pin 47 = 13VDC? No No +5V at U200 Pins 13 & 30? Is 16.8MHz Signal at U200 Pin 19? No Is 16.8MHz signal at U200 pin 23? Yes Yes Replace U200 No Yes Check Y201 and associated parts Check 5V Regulator U503 Check R228 Is U201 Pin 19 <40 mVDC in RX & >4.5 VDC in TX? (at VCO section) Are signals at Pins 14 & 15 of U200? No No Yes Are Waveforms at Pins 14 & 15 triangular? Yes Is U200 pin 2 >4.5 VDC in Tx & <40 mVDC in Rx Check D200, D201, C2026, C2025, C2024 & C2027 Yes Yes Check R201 No No Replace U200 No Is there a short between Pin 47 and Pins 14 & 15 of U200? Yes Is RF level at U200 Pin 32 -12 < x <-25 dBm? Yes Replace U200 No If C2052, R208, C2067 C2068. C210, are OK, then see VCO troubleshooting chart No Check programming lines between U403 and U200 Pins 7,8 & 9 Remove Shorts No Check µP U403 Troubleshooting Chart Do Pins 7,8 & 9 of U200 toggle when channel is changed? Yes Is information from µP U403 correct? Yes Replace U200 3-8 TROUBLESHOOTING CHARTS 4.0 Troubleshooting Flow Chart for VCO RX VCO Low or no RF Signal at input to PA Low or no RF Signal at TP1 Visual check of board OK? NO Correct Problem NO NO Make sure U508 is working correctly and runner between U508 Pin 1 and U201 Pin 14 & 18 is OK NO Make sure Synthesizer is working correctly and runner between U200 Pin 28 and U201 Pin 3 is OK NO NO Check runner between U200 Pin 2 and U201 Pin 19 NO YES Are Q200 Base at 2.4V Collector at 4.5V Emitter at 1.7V NO 4.8V DC at U201 Pin 19 OK? YES NO If all parts associated with the pins are OK Are U201 Pins 13 at 4.4V 15 at 1.1V 10 at 4.5V 16 at 1.9V NO If all parts associated with the pins are OK, replace U201 YES YES If L216, C2071, C2070, Check 9V at R230 NO Is RF available at C2060 YES C2060 are okay replace U201 YES Is RF available at base of Q200 Check Transmiiter Pre Driver YES Check parts between TP1 and Q200 4.5V DC at U201 Pin 3 OK? YES YES 35mV DC at U201 Pin 19 OK? 5V DC at U201 Pin 14 & 18 OK? YES YES 4.5V DC at U201 Pin 3 OK? Visual check of board OK? YES YES 3.3 DC at U201 Pin 14 & 18 OK? TX VCO NO If all parts from U200 Pin 8 to Base of Q200 are OK, replace U200 Power OK but no modulation NO Audio =180mVrms at “+” side of D205 Replace R212 YES 2.5VDC at D205 YES If R211 is Ok, replace D205 NO Replace R211 Troubleshooting Flow Chart for DC Supply (1 of 2) 5.0 3-9 Troubleshooting Flow Chart for DC Supply (1 of 2) Since the failure of a critical voltage supply might cause the radio to automatically power down, supply voltages should first be probed with a multimeter. If all the board voltages are absent, then the voltage test point should be retested using a rising-edge-triggered oscilloscope. If the voltage is still absent, then another voltage should be tested using the oscilloscope. If that voltage is present, then the original voltage supply in question is defective and requires investigation of associated circuitry. 5V Check VDC on C5006 Go to 3V Replace U503 Yes Yes V=5V ? 9v 1 GHz Adjacent Channel Power -60dB @12.5, -70dB @ 20/25kHz Audio Response: ( 300 to 3000Hz) +1, -3dB Audio Distortion: @ 1000 Hz, 60% Rated Maximum Deviation: 3% Typical Receiver Specification Sensitivity (12dBSINAD): (ETS) Intermodulation : (ETS) Adjacent Channel Selectivity: (ETS) Spurious Rejection: (ETS) Rated Audio: (ETS) (Extended audio with 4 Ohm speaker) Audio Distortion @ Rated Audio: Midband 0.35µV (12.5kHz) 0.30µV (25kHz) Typical >65dB 70 dB @ 25 kHz 60 dB @ 12.5 kHz 70 dB 4W Internal , 13W External 3% Typical Hum and Noise: -40 dB @ 12.5 kHz -45 dB @ 20/25 kHz Audio Response: ( 300 to 3000Hz) +1, -3dB Conducted Spurious Emission per FCC Part 15: -57 dBm <1 GHz -47 dBm >1 GHz *Availability subject to the laws and regulations of individual countries. 1-4 MODEL CHART AND TECHNICAL SPECIFICATIONS Chapter 2 THEORY OF OPERATION 1.0 Introduction This Chapter provides a detailed theory of operation for the Midband circuits in the radio. Details of the theory of operation and trouble shooting for the the associated Controller circuits are included in this Section of the manual. 2.0 Midband (66-88MHz) Receiver 2.1 Receiver Front-End The received signal from the antenna connector is filtered by the harmonic filter (common to both receive and transmit) and routed to the front end via the antenna switch. The signal is routed to 2pole pre-selector filter tuned by a dual varacter diode D2301, and on to the LNA, Q2301. This is followed by a 3dB attenuator and a 2-pole post selector filter, tuned by varactor D2304. The varactor control voltage is generated by a DAC in the ASFIC (U504-6). An inverting op-amp stage (U517) amplifies the control signal to provide 0-8V. Signal RX_FE_TUNE voltage is increased under software control for higher receive frequencies. Note that the same DAC is used to control the transmitter power. The 9V supply to the LNA (Q2301) is turned on by Q4 when RX_EN is high. Q2302 controls the biasing so that Q2301 is operated with a constant collector current (15mA). In Local Mode, attenuator R38 improves the intermodulation performance prior to the first mixer. In Distance Mode, normal operation, R38 is bypassed by diode D1, which is forward biassed by Q1 turning on when the LOC_DIST line from the microprocessor (U403-45) is high. The first mixer is a passive, double-balanced type, consisting of T1, T2 and U1. This mixer provides all of the necessary rejection of the half-IF spurious response. High-side injection at +15 dBm is delivered to the first mixer. The mixer output is then connected to a duplex network which matches its output to the XTAL filter input (FL2201) at the IF frequency of 21.4 MHz. The duplex network terminates into a 50 ohm resistor (R41) at all other frequencies. Antenna Front Filter RX_FE_TUNE 12.5kHzFilter 12.5kHzFilter LNA Second Filter Mixer Xtal Filter IF Amp 25kHzFilter First LO Xtal Filter 2nd LO Xtal Osc 25kHzFilter IFIC Phase Shift Element Controller Figure 2-1 Midband Receiver Block Diagram 2-2 THEORY OF OPERATION 2.2 Receiver Back End The IF signal from the crystal filter enters the IF amplifier which provides 20 dB of gain and feeds the IF IC (U2) at pin 1. The first IF signal at 21.4 MHz mixes with the second local oscillator (LO) at 20.945 MHz to produce the second IF at 455 kHz. The second LO uses the external crystal Y2. The second IF signal is amplified and filtered by two external ceramic filters (FL4/FL3 for 12.5KHz channel spacing and FL5/FL2 for 25KHz channel spacing). The IF IC demodulates the signal by means of a quadrature detector and feeds the detected audio (via pin 7) to the audio processing circuits. At IF IC pin 5, an RSSI signal is available with a dynamic range of 70 dB. 3.0 Midband Transmitter Power Amplifier (66-88 MHz) The radio’s 25W PA is a three-stage amplifier used to amplify the output from the TX_INJ to the antenna port. All three stages utilize LDMOS technology. The gain of the first stage (U101)and the second stage (Q105) is adjustable and is controlled by pin 7 of U103-2 via U103-3 and U102-1. It is followed by an LDMOS final stage Q100. Pin Diode Antenna Switch From VCO (TX_INJ) Controlled Stage PA Driver PA-Final Stage Antenna Harmonic Filter RF Jack Coupler Bias Forward A S FI C _C M P SPI BUS PA PWR SET L oo p C ont r ol le r U 103 - 2 Temperature Sense Figure 2-2 Midband Transmitter Block Diagram Devices U101, Q105 and Q100 are surface mounted. When assembled, Q100 is in direct contact with the chassis. Heat spreader M105 ensures good thermal contact for Q105. 3.1 First Power Controller Stage The first stage (U101) is a variable gain integrated circuit containing two LDMOS FET amplifier stages which can provide up to 20dB gain. It amplifies the RF signal from the VCO (TX_INJ). The output power of stage U101 is controlled by a DC voltage applied to pin 1 from the op-amp U103-3, pin 8. The control voltage simultaneously varies the bias of two FET stages within U101. This biasing point determines the overall gain of U101 and therefore its output drive level to Q105, which in turn controls the output power of the PA. Midband Transmitter Power Amplifier (66-88 MHz) 2-3 For a given control voltage input on VCNTR1, Op-amp U103-3 monitors the drain current of U101 via resistor R122 and adjusts the bias voltage of U101 accordingly. In receive mode, the DC voltage from RX_EN line turns on Q101, grounding VCNTR1, which in turn switches off the biasing voltage to U101. 3.2 Power Controlled Driver Stage The next stage is an LDMOS device (Q105) which provides a gain of up to 15dB. This device requires a positive gate bias and a quiescent current flow for proper operation. The bias is set during transmit mode by the drain current control op-amp U102-1, and fed to the gate of Q105 via the resistive network (R175, R147, R178, R179). For a given control voltage input on VCNTR2, Op-amp U102-1 monitors the drain current of Q105 via resistors R126-7 and adjusts the bias voltage of Q105 so that the current remains constant. In receive mode the DC voltage from RX_EN line turns on Q102, grounding VCNTR1, which in turn switches off the biasing voltage to Q105. 3.3 Final Stage The final stage is an LDMOS device (Q100) providing a gain of 12dB. This device also requires a positive gate bias and a quiescent current flow for proper operation. The voltage of the line PA_BIAS is set in transmit mode by the ASFIC and fed to the gate of Q100 via the resistive network R134, R131. This bias voltage is tuned in the factory. If the transistor is replaced, the bias voltage must be tuned using the Tuner. Care must be taken not to damage the device by exceeding the maximum allowed bias voltage. The device’s drain current is drawn directly from the radio’s DC supply voltage input, B+, via L117 and L115. The output matching network transforms the impedance to 50 ohms and feeds the directional coupler. 3.4 Bi-Directional Coupler The bi-directional Coupler is a microstrip printed circuit, which couples a small amount of the forward and reverse power of the RF power from Q100.The coupled signal is rectified to an output power which is proportional to the DC voltage rectified by diode D105; and the resulting DC voltage is routed to the power control section to ensure that the forward power out of the radio is held to a constant value. 3.5 Antenna Switch The antenna switch utilizes the existing dc feed (B+) to the last stage device (Q100). In transmit mode, both PIN diodes (D103, D104) are forward biased. This is achieved by pulling down the voltage at the cathode end of D104 to around 12.4V (0.7V drop across each diode). The current through the diodes needs to be set at around 100 mA to fully open the transmit path through resistor R108. Q106 is a current source controlled by Q103 which is turned on in Tx mode by TX_EN. VR102 ensures that the voltage at resistor R107 never exceeds 5.6V, limiting the current to approximately 100mA. 2-4 3.6 THEORY OF OPERATION Harmonic Filter Inductors L1511, L1512, L1513 and L1515 along with capacitors C1518 to C1523, C1528, C1532 to C1535, C1537 to C1539 and C1542 form a 9-element elliptical low-pass filter to attenuate harmonic energy coming from the transmitter. Resistor R152 drains any electrostatic charges that might otherwise build up on the antenna. The harmonic filter also prevents high level RF signals above the receiver passband from reaching the receiver circuits to improve spurious response rejection. 3.7 Power Control The output power is regulated by using a forward power detection control loop. A directional coupler samples a portion of the forward and reflected RF power. The forward sampled RF is rectified by diode D105, and the resulting DC voltage is routed to the operational amplifier U100. The error output current is then routed to an integrator, and converted into the control voltage. This voltage controls the bias of the pre-driver (U101) and driver (Q105) stages. The output power level is set by way of a DAC, PWR_SET, in the ASFIC (U504), which acts as the forward power control loop reference. The sampled reflected power is rectified by diode D107,The resulting DC voltage is amplified by an operational amplifier U100 and routed to the summing junction. This detector protects the final stage Q100 from reflected power by increasing the error current. The temperature sensor protects the final stage Q100 from overheating by increasing the error current. A thermistor RT100 measures the final stage Q100 temperature. The voltage divider output is routed to an operational amplifier U103 and then goes to the summing junction. The Zener Diode VR101 keeps the loop control voltage below 5.6V and eliminates the DC current from the 9.3 regulator U501. Two local loops for the Pre Driver (U101) and for the Driver (Q105) are used in order to stabilize the current for each stage. In Rx mode, the two transistors Q101 and Q102 go to saturation and shut down the transmitter by applying ground to the Pre Driver U101 and for the Driver Q105 control. VR103, VR104 and Q104, Q108, Q109 and associated circuitry provide protection during load dump transients. 4.0 Midband (66-88MHz) Frequency Synthesis The synthesizer consists of a reference oscillator (Y202), low voltage Fractional-N (LVFRAC-N) synthesizer (U200), and a voltage controlled oscillator (VCO) (Q2741/Q2751). 4.1 Reference Oscillator The reference oscillator is a crystal (Y202) controlled Colpitts oscillator and has a frequency of 16.8MHz. The oscillator transistor and start-up circuit are located in the LVFRAC-N (U200) while the oscillator feedback capacitors, crystal, and tuning varactors are external. An analog-to-digital (A/D) converter internal to the LVFRAC-N (U200) and controlled by the microprocessor via SPI sets the voltage at the warp output of U200 pin 25. This sets the frequency of the oscillator. Consequently, the output of the crystal Y202 is applied to U200 pin 23. Midband (66-88MHz) Frequency Synthesis 2-5 The method of temperature compensation is to apply an inverse Bechmann voltage curve, which matches the crystal’s Bechmann curve to a varactor that constantly shifts the oscillator back on frequency. The crystal vendor characterizes the crystal over a specified temperature range and codes this information into a bar code that is printed on the crystal package. In production, this crystal code is read via a 2-dimensional bar code reader and the parameters are saved. This oscillator is temperature compensated to an accuracy of +/-2.5 PPM from -30 to 60 degrees C. The temperature compensation scheme is implemented by an algorithm that uses five crystal parameters (four characterize the inverse Bechmann voltage curve and one for frequency accuracy of the reference oscillator at 25 degrees C). This algorithm is implemented by the LVFRAC-N (U200) at the power up of the radio. 4.2 Fractional-N Synthesizer The LVFRAC-N U200 consists of a pre-scaler, programmable loop divider, control divider logic, phase detector, charge pump, A/D converter for low frequency digital modulation, balanced attenuator used to balance the high and low frequency analog modulation, 13V positive voltage multiplier, serial interface for control, and a super filter for the regulated 9 volts. DATA (U403 PIN 100) CLOCK (U403 PIN 1) +9V CSX (U403 PIN 2) MOD IN (U501 PIN 40) +5V (U503 PIN 1) +5V (U503 PIN 1) 7 8 30 9 10 13 5, 20, 34, 36 REFERENCE OSCILLATOR 23 24 VOLTAGE MULTIPLIER FREFOUT CLK GND CEX MODIN VCC, DC5V IOUT IADAPT VDD, DC5V MODOUT XTAL1 U200 XTAL2 FRACTIONAL-N SYNTHESIZER 25 WARP 32 PREIN 47 LOCK DATA LOW VOLTAGE VCP VMULT2 14 15 48 43 45 LOOP FILTER STEERING LINE 41 AUX3 2 AUX1 BIAS2 FREF (U504 PIN 34) 6, 22, 33, 44 3 1 BIAS1 LOCK (U403 PIN 56) 19 AUX4 AUX2 SFOUT VMULT1 4 NC NC TRB VCO Bias LO RF INJECTION VOLTAGE 28 FILTERED 9V CONTROLLED OSCILLATOR 40 TX RF INJECTION (1ST STAGE OF PA) 39 BWSELECT To IF Section PRESCALER IN Figure 2-3 Midband Synthesizer Block Diagram A voltage of 9.3V applied to the super filter input (U200, pin 30) supplies an output voltage of 8.6Vdc (VSF) at U200, pin 28. This supplies 8.6 V to the two VCO circuits. To generate a high voltage to supply the phase detector (charge pump) output stage at pin VCP (U200, pin 47) while using a low voltage 5Vdc supply, a 13V positive voltage multiplier is used (D200, D201, and capacitors C2024, 2025, 2026, 2055, 2027, 2001). Output lock (U200, pin 4) provides information about the lock status of the synthesizer loop. A high level at this output indicates a stable loop. A 16.8 MHz reference frequency is provided at U200, pin 19. 2-6 4.3 THEORY OF OPERATION Voltage Controlled Oscillator (VCO) The Voltage Controlled Oscillator (VCO) uses 2 colpitts oscillators, FET Q2741 for transmit and FET Q2751 for receive. The appropriate oscillator is switched on or off by LVFRAC-N IC output AUX3 (U200-2) using transistors Q2742 and Q2752. In RX mode AUX3 is nearly at ground level and Q2742 enables a current flow from the source of FET Q2751 while Q2752 is switched off. In TX mode AUX3 is about 3.3V DC and Q2742 is switched off. Q2752 is switched on and enables a current flow from the source of FET Q2741 while Q2751 is switched off. When switched on the FETs draw a drain current of 8 mA from the LVFRAC-N IC super filter output. The frequency of the receive oscillator is mainly determined by L2752, L2753, C2752 - C2756 and varactor diodes D2751 / D2752. Diode D2754 controls the amplitude of the oscillator. The frequency of the transmit oscillator is mainly determined by L2734, C2736 - C2740 and varactor diodes D2732 / D2733. Diode D2739 controls the amplitude of the oscillator. With a steering voltage from 3V to 10V at the varactor diodes the RX frequency range from 87.4 MHz to 109.4 MHz and the TX frequency range from 66 MHz to 88 MHz are covered. In TX mode the modulation signal coming from the LVFRAC-N synthesizer IC (U200 pin 41) modulates the TX VCO via varactor diode D2731. V-SF STEERING LINE 5V Q2741 MOD OUT U200-41 5V 9V Q2760 Q2770 V-SF TX_EN Q2780 Q2751 TRB U200-2 Q2790 9V SWITCHING CONTROL PRE-SCALER TO U200-32 TX_INJ RX_INJ (Ist LO) Figure 2-4 Midband VCO Block Diagram Both oscillator outputs are combined and buffered by the VCO Buffer Q2760. Q2760 draws a collector current of 13 mA from the stabilized 5V and drives the Mixer Buffer Q2770. Q2770 draws a collector current of 19 mA from the 9V3 voltage and drives the PA Buffer Q2780 (Pout = 13dBm) and the Pre-scaler Buffer Q2790. Q2790 draws a collector current of 8 mA from the stabilized 5V and drives the pre-scaler internal to the LVFRAC-N IC. In transmit mode, the 9.3V supply for the TX PA Buffer Q2780 , is turned on by Q2791. PA Buffer Q2780 draws a collector current of 19mA. The injection signal RX_INJ with a level of 10dBm feeds the mixer through R2774. The buffer stages Q2760, Q2770, Q2780 and the feedback amplifier Q2790 provide the necessary gain and isolation for the synthesizer loop. Midband (66-88MHz) Frequency Synthesis 4.4 2-7 Synthesizer Operation The synthesizer consists of a low voltage FRAC-N IC (LVFRAC-N), reference oscillator, charge pump circuits, loop filter circuit, and DC supply. The output from the pre-scaler buffer (Q2790) is fed to the PREIN, pin 32 of U200 via a low pass filter which attenuates harmonics and provides a correct input level to the LVFRAC-N in order to close the synthesizer loop. The pre-scaler in the synthesizer (U200) is a dual modulus pre-scaler with selectable divider ratios. The divider ratio of the pre-scaler is controlled by the loop divider, which in turn receives its inputs via the SPI. The output of the pre-scaler is applied to the loop divider. The output of the loop divider is connected to the phase detector, which compares the loop divider’s output signal with the reference signal. The reference signal is generated by dividing down the signal of the reference oscillator (Y202). The output signal of the phase detector is a pulsed dc signal that is routed to the charge pump. The charge pump outputs a current from U200, pin 43 (IOUT). The loop filter (consisting of R224, R217, R234, C2074, C2078, C2028, and L205) transforms this current into a voltage that is applied the varactor diodes D2751, D2752 for Rx and D2732, D2733 for Tx. The output frequency is determined by this control voltage. The current can be set to a value fixed in the LVFRAC-N or to a value determined by the currents flowing into BIAS 1 (U200, pin 40) or BIAS 2 (U200, pin 39). The currents are set by the value of R200 or R206 respectively. The selection of the three different bias sources is done by software programming. To modulate the synthesizer loop, a two-spot modulation method is utilized via the MODIN (U200, pin 10) input of the LVFRAC-N. The audio signal is applied to both the A/D converter (low frequency path) and the balance attenuator (high frequency path). The A/D converter converts the low frequency analog modulating signal into a digital code which is applied to the loop divider, thereby causing the carrier to deviate. The balance attenuator is used to adjust the VCO’s deviation sensitivity to high frequency modulating signals. The output of the balance attenuator is presented at the MODOUT port of the LVFRAC-N (U200 pin 41) and connected to the VCO modulation varactor D2731. 2-8 5.0 THEORY OF OPERATION Controller Theory of Operation This section provides a detailed theory of operation for the radio and its components. The main radio is a single-board design, consisting of the transmitter, receiver, and controller circuits. A control head is connected by an extension cable. The control head contains LED indicators, a microphone connector, buttons, and speaker. In addition to the power cable and antenna cable, an accessory cable can be attached to a connector on the rear of the radio. The accessory cable enables you to connect accessories to the radio, such as an external speaker, emergency switch, foot-operated PTT, and ignition sensing, etc. External Microphone To Synthesizer Mod Out 16.8 MHz Reference Clock from Synthesizer Audio/Signaling Architecture Disc Audio ASFIC_CMP . Internal Microphone External Speaker Audio PA Internal Speaker µP Clock SPI To RF Section Digital Architecture SCI to Accessory & Control Head Connector RAM EEPROM 3.3V Regulator HC11FL0 FLASH Figure 2-5 Controller Block Diagram 5.1 Radio Power Distribution Voltage distribution is provided by five separate devices: ■ U514 P-cH FET - Batt + (Ext_SWB+) ■ U501 LM2941T - 9.3V ■ U503 LP2951CM - 5V ■ U508 MC 33269DTRK - 3.3V ■ U510 LP2986ILDX - 3.3V Digital Handset Controller Theory of Operation 2-9 The DC voltage applied to connector P2 supplies power directly to the following circuitry: ■ Electronic on/off control ■ RF power amplifier ■ 12 volts P-cH FET -U514 ■ 9.3 volt regulator ■ Audio PA Ignition Auto On/Off Switch Control B+ Control Head RF_PA Audio_PA Mic Connector Ferrite Bit Filt_B+ Antenna Switch Power Control 500mA FET P-CH On/Off Control SW_Filt_B+ 11-16.6V 0.9A Status LEDs 7_Seg 7_Seg DOT Bed to 7-Seg Back light Shift Reg Acces Conn Audio PA_Soutdown Power Loop Op_Amp 9.3V 65mA U501 9.3V Regulator Keypad Mic Bias 9V, 5mA 0.85A Reset 9.3V 45mA On/Off Control U503 5V RF Regulator 500mA Rx_Amp PA_Pre-driver PA Driver 3.2V 72mA 45mA LVFRAC_N IF_Amp 9.3V 75mA 9.3V 162mA U508 3.3V RF Reg 50mA 25mA ASFIC_CMP IFIC RX Cct U510 3.3V D Reg 90mA micro P RAM Flash EEPROM Figure 2-6 DC Power Distribution Block Diagram Regulator U501 is used to generate the 9.3 volts required by some audio circuits, the RF circuitry and power control circuitry. Input and output capacitors are used to reduce high frequency noise. Resistors R5001 / R5081 set the output voltage of the regulator. This regulator output is electronically enabled by a 0 volt signal on pin 2. Q502, Q505 and R5038 are used to disable the regulator when the radio is turned off. Voltage regulator U510 provides 3.3 volts for the digital circuitry. Operating voltage is from the regulated 9.3V supply. Input and output capacitors are used to reduce high frequency noise and provide proper operation during battery transients. U510 provides a reset output that goes to 0 volts if the regulator output goes below 3.1 volts. This is used to reset the controller to prevent improper operation. Voltage regulator U508 provides 3.3V for the RF circuits and ASFIC_CMP. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. 2-10 THEORY OF OPERATION Voltage regulator U503 provides 5V for the RF circuits. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. VSTBY is used only for CM360 5-tone radios. The voltage VSTBY, which is derived directly from the supply voltage by components R5103 and VR502, is used to buffer the internal RAM. Capacitor C5120 allows the battery voltage to be disconnected for a couple of seconds without losing RAM parameters. Dual diode D501 prevents radio circuitry from discharging this capacitor. When the supply voltage is applied to the radio, C5120 is charged via R5103 and D501. 5.2 Protection Devices Diode VR500 acts as protection against ESD, wrong polarity of the supply voltage, and load dump. VR692 - VR699 are for ESD protection. 5.3 Automatic On/Off The radio can be switched ON in any one of the following ways: 5.3.1 ■ On/Off switch. (No Ignition Mode) ■ Ignition and On/Off switch (Ignition Mode) ■ Emergency No Ignition Mode When the radio is connected to the car battery for the first time, Q500 will be in saturation, Q503 will cut-off, Filt_B+ will pass through R5073, D500, and S5010-pin 6 (On/Off switch). When S5010 is ON, Filt_B+ will pass through S5010-pin5, D511, R5069, R5037 and base of Q505 and move Q505 into saturation. This pulls U501-pin2 through R5038, D502 to 0.2V and turns On U514 and U501 9.3V regulator which supplies voltage to all other regulators and consequently turns the radio on, When U504 (ASFIC_CMP) gets 3.3V, GCB2 goes to 3.3V and holds Q505 in saturation, for soft turn off. 5.3.2 Ignition Mode When ignition is connected for the first time, it will force high current through Q500 collector, This will move Q500 out of saturation and consequently Q503 will cut-off. S5010 pin 6 will get ignition voltage through R601 (for load dump), R610, (R610 & C678 are for ESD protection), VR501, R5074, and D500. When S5010 is ON, Filt_B+ passes through S5010-pin 5, D511, R5069, R5037 and base of Q505 and inserts Q505 into saturation. This pulls U501-pin 2 through R5038, D502 to 0.2V and turns on U514 and U501 9.3V regulator which supply voltage to all other regulators and turns the radio on, When U504 (ASFIC_CMP) get 3.3V supply, GCB2 goes to 3.3V and holds Q505 in saturation state to allow soft turn off, When ignition is off Q500, Q503 will stay at the same state so S5010 pin 6 will get 0V from Ignition, Q504 goes from Sat to Cut, ONOFF_SENSE goes to 3.3V and it indicates to the radio to soft turn itself by changing GCB2 to ‘0’ after de registration if necessary. Controller Theory of Operation 5.3.3 2-11 Emergency Mode The emergency switch (P1 pin 9), when engaged, grounds the base of Q506 via EMERGENCY _ACCES_CONN. This switches Q506 to off and consequently resistor R5020 pulls the collector of Q506 and the base of Q506 to levels above 2 volts. Transistor Q502 switches on and pulls U501 pin2 to ground level, thus turning ON the radio. When the emergency switch is released R5030 pulls the base of Q506 up to 0.6 volts. This causes the collector of transistor Q506 to go low (0.2V), thereby switching Q502 to off. While the radio is switched on, the µP monitors the voltage at the emergency input on the accessory connector via U403-pin 62. Three different conditions are distinguished: no emergency kit is connected, emergency kit connected (unpressed), and emergency press. If no emergency switch is connected or the connection to the emergency switch is broken, the resistive divider R5030 / R5049 will set the voltage to about 3.14 volts (indicates no emergency kit found via EMERGENCY_SENSE line). If an emergency switch is connected, a resistor to ground within the emergency switch will reduce the voltage on EMERGENCY _SENSE line, and indicate to the µP that the emergency switch is operational. An engaged emergency switch pulls line EMERGENCY _SENSE line to ground level. Diode VR503 limits the voltage to protect the µP input. While EMERGENCY _ACCES_CONN is low, the µP starts execution, reads that the emergency input is active through the voltage level of µP pin 64, and sets the DC POWER ON output of the ASFIC CMP pin 13 to a logic high. This high will keep Q505 in saturation for soft turn off. 5.4 Microprocessor Clock Synthesiser The clock source for the µP system is generated by the ASFIC CMP (U504). Upon power-up the synthesizer IC (FRAC-N) generates a 16.8 MHz waveform that is routed from the RF section to the ASFIC CMP pin 34. For the main board controller the ASFIC CMP uses 16.8 MHz as a reference input clock signal for its internal synthesizer. The ASFIC CMP, in addition to audio circuitry, has a programmable synthesizer which can generate a synthesized signal ranging from 1200Hz to 32.769MHz in 1200Hz steps. When power is first applied, the ASFIC CMP will generate its default 3.6864MHz CMOS square wave UP CLK (on U504 pin 28) and this is routed to the µP (U403 pin 90). After the µP starts operation, it reprograms the ASFIC CMP clock synthesizer to a higher UP CLK frequency (usually 7.3728 or 14.7456 MHz) and continues operation. The ASFIC CMP may be reprogrammed to change the clock synthesizer frequencies at various times depending on the software features that are executing. In addition, the clock frequency of the synthesizer is changed in small amounts if there is a possibility of harmonics of the clock source interfering with the desired radio receive frequency. The ASFIC CMP synthesizer loop uses C5025, C5024 and R5033 to set the switching time and jitter of the clock output. If the synthesizer cannot generate the required clock frequency it will switch back to its default 3.6864MHz output. Because the ASFIC CMP synthesizer and the µP system will not operate without the 16.8 MHz reference clock it (and the voltage regulators) should be checked first when debugging the system. 2-12 5.5 THEORY OF OPERATION Serial Peripheral Interface (SPI) The µP communicates to many of the IC’s through its SPI port. This port consists of SPI TRANSMIT DATA (MOSI) (U403-pin100), SPI RECEIVE DATA (MISO) (U403-pin 99), SPI CLK (U0403-pin1) and chip select lines going to the various IC’s, connected on the SPI PORT (BUS). This BUS is a synchronous bus, in that the timing clock signal CLK is sent while SPI data (SPI TRANSMIT DATA or SPI RECEIVE DATA) is sent. Therefore, whenever there is activity on either SPI TRANSMIT DATA or SPI RECEIVE DATA there should be a uniform signal on CLK. The SPI TRANSMIT DATA is used to send serial from a µP to a device, and SPI RECEIVE DATA is used to send data from a device to a µP. There are two IC’s on the SPI BUS, ASFIC CMP (U504 pin 22)), and EEPROM (U400). In the RF sections there is one IC on the SPI BUS, the FRAC-N Synthesizer. The chip select line CSX from U403 pin 2 is shared by the ASFIC CMP and FRAC-N Synthesizer. Each of these IC’s check the SPI data and when the sent address information matches the IC’s address, the following data is processed. When the µP needs to program any of these Is it brings the chip select line CSX to a logic “0” and then sends the proper data and clock signals. The amount of data sent to the various IC’s are different; e.g., the ASFIC CMP can receive up to 19 bytes (152 bits). After the data has been sent the chip select line is returned to logic “1”. 5.6 SBEP Serial Interface The SBEP serial interface allows the radio to communicate with the Customer Programming Software (CPS), or the Universal Tuner via the Radio Interface Box (RIB) or the cable with internal RIB. This interface connects to the SCI pin via control head connector (J2-pin 17) and to the accessory connector P1-6 and comprises BUS+. The line is bi-directional, meaning that either the radio or the RIB can drive the line. The µP sends serial data and it reads serial data via pin 97. Whenever the µP detects activity on the BUS+ line, it starts communication. 5.7 General Purpose Input/Output The controller provides six general purpose lines (PROG I/O) available on the accessory connector P1 to interface to external options. Lines PROG IN 3 and 6 are inputs, PROG OUT 4 is an output and PROG IN OUT 8, 12 and 14 are bi-directional. The software and the hardware configuration of the radio model define the function of each port. ■ PROG IN 3 can be used as external PTT input, or others, set by the CPS. The µP reads this port via pin 72 and Q412. ■ PROG OUT 4 can be used as external alarm output, set by the CPS. Transistor Q401 is controlled by the µP (U403 pin 55) ■ PROG IN 6 can be used as normal input, set by the CPS. The µP reads this port via pin 73 and Q411. This pin is also used to communicate with the RIB if resistor R421 is placed. ■ DIG IN OUT 8,12,14 are bi-directional and use the same circuit configuration. Each port uses an output Q416, Q404, Q405 controlled by µP pins 52, 53, 54. The input ports are read through µP pins 74, 76, 77; using Q409, Q410, Q411 Controller Theory of Operation 5.8 2-13 Normal Microprocessor Operation For this radio, the µP is configured to operate in one of two modes, expanded and bootstrap. In expanded mode the µP uses external memory devices to operate, whereas in bootstrap operation the µP uses only its internal memory. In normal operation of the radio the µP is operating in expanded mode as described below. During normal operation, the µP (U403) is operating in expanded mode and has access to 3 external memory devices; U400 (EEPROM), U402 (SRAM), U404 (Flash). Also, within the µP there are 3 Kilobytes of internal RAM, as well as logic to select external memory devices. The external EEPROM (U400) space contains the information in the radio which is customer specific, referred to as the codeplug. This information consists of items such as: 1) what band the radio operates in, 2) what frequencies are assigned to what channel, and 3) tuning information. The external SRAM (U402) as well as the µP’s own internal RAM space are used for temporary calculations required by the software during execution. All of the data stored in both of these locations is lost when the radio powers off. The µP provides an address bus of 16 address lines (ADDR 0 - ADDR 15), and a data bus of 8 data lines (DATA 0 - DATA 7). There are also 3 control lines; CSPROG (U403-38) to chip select U404-pin 30 (FLASH), CSGP2 (U403-pin 41) to chip select U404-pin 20 (SRAM) and PG7_R_W (U403-pin 4) to select whether to read or to write. The external EEPROM (U400-pin1). When the µP is functioning normally, the address and data lines should be toggling at CMOS logic levels. Specifically, the logic high levels should be between 3.1 and 3.3V, and the logic low levels should be between 0 and 0.2V. No other intermediate levels should be observed, and the rise and fall times should be <30ns. The low-order address lines (ADDR 0 - ADDR 7) and the data lines (DATA 0-DATA 7) should be toggling at a high rate, e.g., you should set your oscilloscope sweep to 1us/div. or faster to observe individual pulses. High speed CMOS transitions should also be observed on the µP control lines. On the µP the lines XIRQ (U403-pin 48), MODA LIR (U403-pin 58), MODB VSTPY (U403-pin 57) and RESET (U403-pin 94) should be high at all times during normal operation. Whenever a data or address line becomes open or shorted to an adjacent line, a common symptom is that the RESET line goes low periodically, with the period being in the order of 20ms. In the case of shorted lines you may also detect the line periodically at an intermediate level, i.e. around 2.5V when two shorted lines attempt to drive to opposite rails. The MODA LIR (U403-pin 58) and MODB VSTPY (U403-pin 57) inputs to the µP must be at a logic “1” for it to start executing correctly. After the µP starts execution it will periodically pulse these lines to determine the desired operating mode. While the Central Processing Unit (CPU) is running, MODA LIR is an open-drain CMOS output which goes low whenever the µP begins a new instruction. An instruction typically requires 2-4 external bus cycles, or memory fetches. There are eight analog-to-digital coverter ports (A/D) on U403 labelled within the device block as PEO-PE7. These lines sense the voltage level ranging from 0 to 3.3V of the input line and convert that level to a number ranging from 0 to 255 which is read by the software to take appropriate action. 2-14 5.9 THEORY OF OPERATION Static Random Access Memory (SRAM) The SRAM (U402) contains temporary radio calculations or parameters that can change very frequently, and which are generated and stored by the software during its normal operation. The information is lost when the radio is turned off. The device allows an unlimited number of write cycles. SRAM accesses are indicated by the CS signal U402 (which comes from U403-CSGP2) going low. U402 is commonly referred to as the external RAM as opposed to the internal RAM which is the 3 Kilobytes of RAM which is part of the 68HC11FL0. Both RAM spaces serve the purpose. However, the internal RAM is used for the calculated values which are accessed most often. Capacitor C402 and C411 serves to filter out any AC noise which may ride on +3.3 V at U402 6.0 Control Board Audio and Signalling Circuits 6.1 Audio Signalling Filter IC and Compander (ASFIC CMP) The ASFIC CMP (U504) used in the controller has the following four functions: 1. RX/TX audio shaping, i.e. filtering, amplification, attenuation 2. RX/TX signaling, PL/DPL/HST/MDC 3. Squelch detection 4. µP clock signal generation The ASFIC CMP is programmable through the SPI BUS (U504 pins-20/21/22), normally receiving 19 bytes. This programming sets up various paths within the ASFIC CMP to route audio and/or signaling signals through the appropriate filtering, gain and attenuator blocks. The ASFIC CMP also has 6 General Control Bits GCB0-5 which are CMOS level outputs and used for the following: ■ GCBO - BW Select ■ GCBI - switches the audio PA On/Off ■ GCB2 - DC Power On switches the voltage regulator (and the radio) on and off ■ GCB3 - Control on MUX U509 pin 9 to select between Low Cost Mic path to STD Mic Path ■ GCB4 - Control on MUX U509 pin 11 to select between Flat RX path to filtered RX path on the accessory connector. ■ GCB5 - Control on MUX U509 pin 10 to select between Flat TX path mute and Flat TX path Transmit Audio Circuits 7.0 2-15 Transmit Audio Circuits J2 24kOhms U509 15 MIC 46 35 P1 48 2 FLAT TX AUDIO MIC INT GCB3 MIC EXT U509 5 36 TX RTN MUX CONTROL HEAD CONNECTOR EXT MIC 44 TX SND 42 MUX AUX TX ACCESSORY CONNECTOR FILTERS AND PREEMPHASIS MIC ASFIC_CMP IN U504 LIMITER HS SUMMER SPLATTER FILTER LS SUMMER 38 GCB5 FLAT TX AUDIO MUTE VCO ATN ATTENUATOR MOD IN 40 TO RF SECTION (SYNTHESIZER) Figure 2-7 Transmit Audio Paths 7.1 Microphone Input Path The radio supports 2 distinct microphone paths known as internal (from control head J2-15) and external mic (from accessory connector P1-2) and an auxiliary path (FLAT TX AUDIO, from accessory connector P1-5). The microphones used for the radio require a DC biasing voltage provided by a resistive network. The two microphone audio input paths enter the ASFIC CMP at U504-pin 48 (external mic) and U504-pin 46 (internal mic). The microphone is plugged into the radio control head and connected to the audio DC via J2-pin 15. The signal is then routed via C5045 to MUX U509 that select between two paths with different gain to support Low Cost Mic (Mic with out amplifier in it) and Standard Mic. 7.1.1 Low Cost Microphone Hook Pin is shorted to Pin 1(9.3V) inside the Low Cost Mic, This routes 9.3V to R429, and creates 2.6V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 = ‘0’. The audio signal is routed from C5045 via U509-5 (Z0), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int. mic (C5046 100nF creates a159Hz pole with U504- 46 int mic impedance of 16Kohm). 2-16 7.1.2 THEORY OF OPERATION Standard Microphone Hook Pin is shorted to the hook mic inside the standard Mic, If the mic is out off hook, 3.3V is routed to R429 via R458, D401, and it create 0.7V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 =‘1’. The audio signal is routed from C5045 via U509-3 (Z1), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int mic (C5046 100nF create a159Hz pole with U504- 46 int mic impedance of 16Kohm). 9.3VDC is routed via R5077, R5075 to J2-15, It create 4.65V with Mic Impedance. C5010 supplies AC Ground to create AC impedance of 510 Ohms via R5075. and Filter 9.3V DC mic bias supply. Note: The audio signal at U504-pin 46 should be approximately 12mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The external microphone signal enters the radio on accessory connector P1 pin 2 and is routed via line EXT MIC to R5054. R5078 and R5076 provide the 9.3Vdc bias. Resistive divider R5054/ R5070 divide the input signal by 5.5 and provide input protection for the CMOS amplifier input. R5076 and C5009 provide a 510 ohm AC path to ground that sets the input impedance for the microphone and determines the gain based on the emitter resistor in the microphone’s amplifier circuit. C5047 serves as a DC blocking capacitor. The audio signal at U504-pin 48 should be approximately 14mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The FLAT TX AUDIO signal from accessory connector P1-pin 5 is fed to the ASFIC CMP (U504 pin 42 through U509 pin 2 to U509 pin 15 via U506 OP-AMP circuit and C5057. The ASFIC has an internal AGC that can control the gain in the mic audio path. The AGC can be disabled / enabled by the µP. Another feature that can be enabled or disabled in the ASFIC is the VOX. This circuit, along with Capacitor C5023 at U504-pin 7, provides a DC voltage that can allow the µP to detect microphone audio. The ASFIC can also be programmed to route the microphone audio to the speaker for public address operation. 7.2 PTT Sensing and TX Audio Processing Internal microphone PTT is sensed by µP U403 pin 71. Radio transmits when this pin is “0” and selects inside the ASFIC_ CMP U504 internal Mic path. When the internal Mic PTT is “0” then external Mic PTT is grounded via D402. External Mic PTT is sensed by U403 pin 72 via Q412 circuits. The radio transmits when this pin is “0” and selects inside the ASFIC _CMP U504 External Mic path. Inside the ASFIC CMP, the mic audio is filtered to eliminate frequency components outside the 3003000Hz voice band, and pre-emphasized if pre-emphasis is enabled. The signal is then limited to prevent the transmitter from over deviating. The limited mic audio is then routed through a summer, which is used to add in signaling data, and then to a splatter filter to eliminate high frequency spectral components that could be generated by the limiter. The audio is then routed to an attenuator, which is tuned in the factory or the field to set the proper amount of FM deviation. The TX audio emerges from the ASFIC CMP at U504-pin 40 MOD IN, at which point it is routed to the RF section. Transmit Signalling Circuits 8.0 2-17 Transmit Signalling Circuits HS SUMMER 44 MICRO CONTROLLER U403 19 HIGH SPEED CLOCK IN (HSIO) DTMF ENCODER 82 SPI BUS SPLATTER FILTER ASFIC_CMP U504 85 80 5-3-2 STATE ENCODER 18 LOW SPEED CLOCK IN (LSIO) PL ENCODER LS SUMMER ATTENUATOR 40 MOD IN TO RF SECTION (SYNTHESIZER) Figure 2-8 Transmit Signalling Path From a hardware point of view, there are 3 types of signaling: ■ Sub-audible data (PL / DPL / Connect Tone) that gets summed with transmit voice or signaling, ■ DTMF data for telephone communication in trunked and conventional systems, and ■ Audible signaling including MDC and high-speed trunking. Note: All three types are supported by the hardware while the radio software determines which signaling type is available. 8.1 Sub-Audio Data (PL/DPL) Sub-audible data implies signaling whose bandwidth is below 300Hz. PL and DPL waveforms are used for conventional operation and connect tones for trunked voice channel operation. The trunking connect tone is simply a PL tone at a higher deviation level than PL in a conventional system. Although it is referred to as “sub-audible data”, the actual frequency spectrum of these waveforms may be as high as 250 Hz, which is audible to the human ear. However, the radio receiver filters out any audio below 300Hz, so these tones are never heard in the actual system. Only one type of sub-audible data can be generated by U504 (ASFIC CMP) at any one time. The process is as follows, using the SPI BUS, the µP programs the ASFIC CMP to set up the proper lowspeed data deviation and select the PL or DPL filters. The µP then generates a square wave which strobes the ASFIC PL / DPL encode input LSIO U504-pin 18 at twelve times the desired data rate. For example, for a PL frequency of 103Hz, the frequency of the square wave would be 1236Hz. This drives a tone generator inside U504 which generates a staircase approximation to a PL sine wave or DPL data pattern. This internal waveform is then low-pass filtered and summed with voice or data. The resulting summed waveform then appears on U504-pin 40 (MOD IN), where it is sent to the RF board as previously described for transmit audio. A trunking connect tone would be generated in the same manner as a PL tone. 2-18 8.2 THEORY OF OPERATION High Speed Data High speed data refers to the 3600 baud data waveforms, known as Inbound Signaling Words (ISWs) used in a trunking system for high speed communication between the central controller and the radio. To generate an ISW, the µP first programs the ASFIC CMP (U504) to the proper filter and gain settings. It then begins strobing U504-pin 19 (HSIO) with a pulse when the data is supposed to change states. U504’s 5-3-2 State Encoder (which is in a 2-state mode) is then fed to the postlimiter summer block and then the splatter filter. From that point it is routed through the modulation attenuator and then out of the ASFIC CMP to the RF board. MDC is generated in much the same way as trunking ISW. However, in some cases these signals may also pass through a data preemphasis block in the ASFIC CMP. Also these signaling schemes are based on sending a combination of 1200 Hz and 1800 Hz tones only. Microphone audio is muted during high speed data signaling. 8.3 Dual Tone Multiple Frequency (DTMF) Data DTMF data is a dual tone waveform used during phone interconnect operation. It is the same type of tones which are heard when using a “Touch Tone” telephone. There are seven frequencies, with four in the low group (697, 770, 852, 941Hz) and three in the high group (1209, 1336, 1477Hz). The high-group tone is generated by the µP (U403-46) strobing U50419 at six times the tone frequency for tones less than 1440Hz or twice the frequency for tones greater than 1440Hz. The low group tone is generated by the ASFIC CMP, controlled by the µP via SPI bus. Inside U504 the low-group and high-group tones are summed (with the amplitude of the high group tone being approximately 2 dB greater than that of the low group tone) and then preemphasized before being routed to the summer and splatter filter. The DTMF waveform then follows the same path as was described for high-speed data. Receive Audio Circuits 9.0 2-19 Receive Audio Circuits ACCESSORY CONNECTOR 11 1 AUDIO PA U502 9 4 SPKR + 16 SPKR - 1 EXTERNAL SPEAKER 6 INT SPKR+ INT SPKRCONTROL HEAD CONNECTOR 19 MUTE U509 FLT RX AUDIO P1 INTERNAL SPEAKER 20 J2 18 HANDSET AUDIO U505 37 39 10 GCB4 U IO 43 AUX RX 14 41 URX OUT AUDIO GCB1 VOLUME ATTEN. ASFIC_CMP U504 FILTER AND DEEMPHASIS DISC FROM AUDIO RF SECTION (IF IC) 2 DISC PL FILTER LIMITER LIMITER, RECTIFIER FILTER, COMPARATOR LS IO 18 SQUELCH CIRCUIT SQ DET CH ACT 16 17 84 83 MICRO CONTROLLER 80 U403 85 Figure 2-9 Receive Audio Paths 9.1 Squelch Detect The radio’s RF circuits are constantly producing an output at the discriminator (IF IC). This signal (DISC AUDIO) is routed to the ASFIC CMP’s squelch detect circuitry input DISC (U504-pin 2). All of the squelch detect circuitry is contained within the ASFIC CMP. Therefore from a user’s point of view, DISC AUDIO enters the ASFIC CMP, and the ASFIC CMP produces two CMOS logic outputs based on the result. They are CH ACT (U504-16) and SQ DET (U504-17). The squelch signal entering the ASFIC CMP is amplified, filtered, attenuated, and rectified. It is then sent to a comparator to produce an active high signal on CH ACT. A squelch tail circuit is used to produce SQ DET (U504-17) from CH ACT. The state of CH ACT and SQ DET is high (logic “1”) when carrier is detected, otherwise low (logic “0”). CH ACT is routed to the µP pin 84 while SQ DET is routed to the µP pin 83. SQ DET is used to determine all audio mute / unmute decisions except for Conventional Scan. In this case CH ACT is a pre-indicator as it occurs slightly faster than SQ DET. 2-20 9.2 THEORY OF OPERATION Audio Processing and Digital Volume Control The receiver audio signal (DISC AUDIO) enters the controller section from the IF IC where it is.DC coupled to ASFIC CMP via the DISC input U504-pin 2. The signal is then applied to both the audio and the PL/DPL paths The audio path has a programmable amplifier, whose setting is based on the channel bandwidth being received, an LPF filter to remove any frequency components above 3000Hz, and a HPF to strip off any sub-audible data below 300Hz. Next, the recovered audio passes through a deemphasis filter (if it is enabled to compensate for Pre-emphasis which is used to reduce the effects of FM noise). The IC then passes the audio through the 8-bit programmable attenuator whose level is set depending on the value of the volume control. Finally the filtered audio signal passes through an output buffer within the ASFIC CMP. The audio signal exits the ASFIC CMP at AUDIO output (U504 pin 41). The µP programs the attenuator, using the SPI BUS, based on the volume setting. The minimum / maximum settings of the attenuator are set by codeplug parameters. Since sub-audible signaling is summed with voice information on transmit, it must be separated from the voice information before processing. Any sub-audible signaling enters the ASFIC CMP from the IF IC at DISC U504-2. Once inside, it goes through the PL/DPL path. The signal first passes through one of the two low-pass filters, either the PL low-pass filter or the DPL/LST low-pass filter. Either signal is then filtered and goes through a limiter and exits the ASFIC CMP at LSIO (U504-pin 18). At this point, the signal will appear as a square wave version of the sub-audible signal which the radio received. The µP U403 pin 80 will decode the signal directly to determine if it is the tone / code which is currently active on that mode. 9.3 Audio Amplification Speaker (+) Speaker (-) The output of the ASFIC CMP’s digital volume pot, U504-pin 41 is routed through DC blocking capacitor C5049 to the audio PA (U502 pin 1 and 9). The audio power amplifier has one inverted and one non-inverted output that produces the differential audio output SPK+/SPK- (U502 pins 4 and 6) The audio PA is enabled via the ASFIC CMP (U504-GCB1). When the base of Q501 is low, the transistor is off and U502-pin 8 is high, using pull up resistor R5041, and the audio PA is ON. The voltage at U502-pin 8 must be above 8.5Vdc to properly enable the device. If the voltage is between 3.3 and 6.4V, the device will be active but has its input (U502-pins 1/9) off. This is a mute condition which is used to prevent an audio pop when the PA is enabled. The SPK+ and SPK- outputs of the audio PA have a DC bias which varies proportionately with B+ (U502- pin 7). B+ of 11V yields a DC offset of 5V, and B+ of 17V yields a DC offset of 8.5V. If either of these lines is shorted to ground, it is possible that the audio PA will be damaged. SPK+ and SPKare routed to the accessory connector (P1-pin 1 and 16) and to the control head (connector J2-pins 19 and 20). Receive Signalling Circuits 9.4 2-21 Handset Audio Certain handheld accessories have a speaker within them which require a different voltage level than that provided by U502. For these devices HANDSET AUDIO is available at control head connector J2 pin18. The received audio from the output of the ASFIC CMP’s digital volume attenuator is routed to U505 pin 2 where it is amplified. This signal is routed from the output of the op-amp U505 to J2-pin 18. From the control head, the signal is sent directly to the microphone jack. 9.5 Filtered Audio and Flat Audio The ASFIC CMP output audio at U504-pin 39 is filtered and de-emphasized, but has not gone through the digital volume attenuator. From ASFIC CMP U504-pin 39 the signal is routed via R5034 through gate U509-pin 12 and AC coupled to U505-pin 6. The gate controlled by ASFIC CMP port GCB4 selects between the filtered audio signal from the ASFIC CMP pin 39 (URXOUT) or the unfiltered (flat) audio signal from the ASFIC CMP pin 10 (UIO). Resistors R5034 and R5021 determine the gain of op-amp UU505-pin 6 for the filtered audio while R5032 and R5021 determine the gain for the flat Audio. The output of U505-pin 7 is then routed to P1 pin 11 via DC blocking capacitor C5003. Note that any volume adjustment of the signal on this path must be done by the accessory. 10.0 Receive Signalling Circuits DATA FILTER AND DEEMPHASIS DET AUDIO DISCRIMINATOR AUDIO FROM RF SECTION (IF IC) 2 LIMITER HSIO 19 82 44 DISC ASFIC_CMP U504 FILTER LIMITER MICRO CONTROLLER U403 LSIO 18 80 85 PLEAP 8 PLCAP2 25 Figure 2-10 Receive Signalling Paths 10.1 Sub-Audio Data (PL/DPL) and High Speed Data Decoder The ASFIC CMP (U504) is used to filter and limit all received data. The data enters the ASFIC CMP at input DISC (U504 pin 2). Inside U504 the data is filtered according to data type (HS or LS), then it is limited to a 0-3.3V digital level. The MDC and trunking high speed data appear at U504-pin 19, where it connects to the µP U403 pin 80. 2-22 THEORY OF OPERATION The low speed limited data output (PL, DPL, and trunking LS) appears at U504-pin18, where it connects to the µP U403-pin 80. The low speed data is read by the µP at twice the frequency of the sampling waveform; a latch configuration in the ASFIC CMP stores one bit every clock cycle. The external capacitors C5028, and C5026 set the low frequency pole for a zero crossings detector in the limiters for PL and HS data. The hysteresis of these limiters is programmed based on the type of received data. 10.2 Alert Tone Circuits When the software determines that it needs to give the operator an audible feedback (for a good key press, or for a bad key press), or radio status (trunked system busy, phone call, circuit failures), it sends an alert tone to the speaker. It does so by sending SPI BUS data to U504 which sets up the audio path to the speaker for alert tones. The alert tone itself can be generated in one of two ways: internally by the ASFIC CMP, or externally using the µP and the ASFIC CMP. The allowable internal alert tones are 304, 608, 911, and 1823Hz. In this case a code contained within the SPI BUS load to the ASFIC CMP sets up the path and determines the tone frequency, and at what volume level to generate the tone. (It does not have to be related to the voice volume setting.) For external alert tones, the µP can generate any tone within the 100-3000Hz audio band. This is accomplished by the µP generating a square wave which enters the ASFIC CMP at U504 pin 19. Inside the ASFIC CMP this signal is routed to the alert tone generator. The output of the generator is summed into the audio chain just after the RX audio de-emphasis block. Inside U504, the tone is amplified and filtered, then passed through the 8-bit digital volume attenuator, which is typically loaded with a special value for alert tone audio. The tone exits at U504pin 41 and is routed to the audio PA like receive audio. Chapter 3 TROUBLESHOOTING CHARTS This section contains detailed troubleshooting flowcharts. These charts should be used as a guide in determining the problem areas. They are not a substitute for knowledge of circuit operation and astute troubleshooting techniques. It is advisable to refer to the related detailed circuit descriptions in the theory of operation sections prior to troubleshooting a radio. Most troubleshooting charts end up by pointing to an IC to replace. It is not always noted, but it is good practice to verify supplies and grounds to the affected IC and to trace continuity to the malfunctioning signal and related circuitry before replacing any IC. For instance, if a clock signal is not available at a destination, continuity from the source IC should be checked before replacing the source IC. 3-2 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for Out-of-Lock Receiver (Sheet 1 of 2) NOTE: HANDLE WITH CARE C2078 (main loop filter capacitor) is easily damaged by heat or soldering START Monitor TP200 at turn-on See figure for typical trace Yes TP200 Is Voltage correct for freq? Typ. 4V for 66MHz to 11v for 88MHz (Rx freq.) Voltage dependent on power-on channel: typ. 3.8v for 66Mhz 10.7V for 88MHz (Rx Freq.) No TP200 Is ramp-up slope correct? Typ.14V in 500ms 500ms turn-on Check C2078, R217, R224, C2074, R200, R234 Check U200-4 (lock detect line) Check U200-45, 43 lines. If all ok, replace U200 typ.14.7V No synth programmed with power-up channel 1.0 Go to ‘A’ sheet 2 of 2 Yes TP200 Does voltage reach typ. 14.7V No Yes Check voltage on U200-47 typ. 14.7V No U200-19 No Go to Ref. should be 16.8MHz, 0.5Vpp Osc.Section Yes Yes Replace U200 Go to Rx VCO Section No Check LO level TP1 approx -18dBm into 50 Ohms No Yes Yes Check D2751, D2752, L2750-L2753, C2751-C2756 No Is freq approx 118MHz TP200 approx 14.7V ? or <75MHz TP200 approx <1V U200-14,15 should be square wave 1.05MHz, 3.6Vpp Yes Check Q2790 and associated cctry check C2796, R2796 Check R228, R225 D200, D201, C2024 -C2027, C2001 Troubleshooting Flow Chart for Out-of-Lock Receiver (Sheet 1 of 2) 1.1 3-3 Troubleshooting Flow Chart for Out-of-Lock Receiver (Sheet 2 of 2) From ‘A’ sheet 1 of 2 TP200 Does Voltage stay <1V ? Yes SPI No activity on U200-7, 8, 9? No Yes 3.3V on U200-5, 20 34, 36? No Check U508 Yes 5V on U200-13? No Check U503 Yes 9.2V on U200-30? No Check R2808, Check U501 No Check C2006, U200-26, if ok replace U200 Yes V-SF 8.7V on U200-28? Yes Check C2078, R234, R217, C2074, R200 If all ok, replace U200 Check SPI Connections Fault in digital area 3-4 2.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 25W Transmitter (Sheet 1 of 4) START Ensure that the radio is set-up via the CPS to have 25W channels No or too low power when keyed Rx sensitivity OK? No Check Harmonic Filter components C1537 to Antenna Connector Yes Check components between Q100 and RF output, Antenna Switch D104, D103, VR102 and Q106, Q103 and associated bias circuitry. Check DC volts present at anode of D103. >1A Current increase when keyed? >800mA & <1A Short U100 Pin 3 to ground <800mA Control Voltage at TP150 >1.6V? No Check 9.3V Regulator U501, R180 & R181 No Voltage U103 pin 5 = 4.7V? Yes Check power settings, tuning, R142, R143, R156 & components between U103 Pin 3 and ASFIC Pin 6 before replacing ASFIC No U103 Pin 3 <2.7Vdc Yes Check U103 Yes PA Bias Voltage@R134 >2Vdc No Check Forward Power Sense Circuit Yes Check PA Stages Yes Voltage at TP150 rises? No Check Forward Power Sense Circuit Troubleshooting Flow Chart for 25W Transmitter (Sheet 1 of 4) 2.1 3-5 Troubleshooting Flow Chart for 25W Transmitter (Sheet 2 of 4) Check PA Stages Quick check of PA devices. Check 13.8v present at drain Q100. Disconnect power supply, measure R131 to Ground. 10kOhm? No Replace Q100. Re-tune PA Bias with Tuner. Yes Measure R147 to Ground. 22kOhm? No Yes Connect power supply. Key radio. Go to ‘A’ sheet 3 of 4 Replace Q105. 3-6 2.2 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 25W Transmitter (Sheet 3 of 4) From ‘A’ sheet 2 of 4 DC Voltage at Q101 & Q102 base=0? Check Q101, Q102, R153, R136, R165, R122, R168 & R137 <2.0V Yes Check U103 before replacing U101 DC Voltage at U103 Pin 8 >5.0V Check resistive network at Pin 9 and 10 of U103 before replacing U101 2.0 to 5.0V Measure DC Voltage at U102 Pin 1 <2V Pin 1 Voltage >3V Check Q102, R139, R166, R126, R169, R138, R175, R147 No DC Voltage at U103 Pin 3 = 8.8V Check U403 Yes No DC Voltage at U103 Pin 10=8.8V No 2-3V Yes Check U102 before replacing Q105 Check Final PA Stages Check resistive network at Pin 2 & 3 of U102 before replacing Q105 Troubleshooting Flow Chart for 25W Transmitter (Sheet 1 of 4) 2.3 3-7 Troubleshooting Flow Chart for 25W Transmitter (Sheet 4 of 4) Check Final PA Stage >100mV & <2V Check voltage varies as bias softpot is tuned (in small steps) via the Global Tuner. Check Bias Tuning, R134, R131, R105 & R106 before replacing ASFIC U504. PA_Bias Voltage at R134 Supply Voltage Replace Q100 or 0V 2-3V RF Voltage after C1044 >100mV? No Check FGU Yes Voltage across R122 >50mV? No Check components between C1044 & C182 No Check components between C182 & Q105 No Check components between Q105 & Q100 Yes RF Voltage Q105 gate >250mV? Yes RF Voltage Q100 gate >1.0V? Yes Check components between Q100 & antenna connector 3-8 3.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for Synthesizer (Reference Oscillator) Incorrect or no µP clock signal TP403 Freq. = 14.7MHz or 7.4MHz ? YES Reference Oscillator working NO TP403 YES Freq. = 3.68MHz Power-up default freq. Fault with ASFIC or Controller section NO Check U504-28 should be 16.8MHz 0.5Vpp YES Check U504 and C504, C5025, R5033 NO Check U504-28 Check Y202-1 should be 16.8MHz 0.5Vpp YES Faulty U200, or R229 NO Check Y201 and associated circuitry Troubleshooting Flow Chart for VCO 4.0 3-9 Troubleshooting Flow Chart for VCO No Receive VCO Signal at TP1 NO >7V at Q2751D ? Power Ok but No modulation Check supply at Q2751 YES NO Audio from U200-11? Check modulation tuning softpots YES NO <0.1V at Q2742-2? Check Q2742, R2743 U200-2 should be 0V Check audio on D2731 and Vdc approx 8.6V NO YES Use Hi - impedance probe to check frequency Is freq. approx 118 MHz? YES NO Check Rx VCO parts Check D27312, R2731, C2734 YES Fault in buffer section Q2760, Q2770 - check supplies and parts Out-of-Lock in TX On detection of an out-of-lock in Tx, the radio returns to the Rx mode. Check Rx - Tx switching Q2742, Q2752 (should be turned on) Check Q2741 and associated circuitry. NOTE: The TX VCO can be force enabled by grounding Q2742-3 Check R2714, C2722, C2731, C2733, L2731 3-10 5.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for Receiver (Sheet 1 of 2) START Ensure that all Power Supplies are correct, as detailed in paragraph 6. Bad SINAD Bad 20dB Quieting No Recovered Audio Audio at pin 8 of U2 ? Yes Check Controller (in the case of no audio) OR ELSE go to “B” No Spray or inject 21.4MHz into XTAL Filter FL3101 Yes B A Check Q6 bias for faults Audio heard ? No No Biasing OK ? Check 2nd LO (20.945MHz) at C53 Replace Q6 B Yes Yes LO present ? No Go to B Check voltages on U2 Check circuitry around U2. Replace U2 if defect No Voltages OK? Yes Check circuitry around Y2 Replace Y2 if defect Troubleshooting Flow Chart for Receiver (Sheet 1 of 2) 5.1 3-11 Troubleshooting Flow Chart for Receiver (Sheet 2 of 2) B Inject RF into J1 Yes IF Signal at C58? Trace IF signal from C58 to Q6. Check for bad XTAL filters IF signal at Q6 collector? No Before replacing U2, check U2 voltages No Yes RF Signal at T1? No 1st LO level OK? Locked? Yes Yes RF Signal at C2337? Yes No Check FGU Check T1, T2, U1 (diode), R41, L2, L2792, C59 and L6 Check filter between C2337 & T1 A No Yes RF Signal at C2308? Check RF amp (Q2301) Stage No or weak RF Yes RF Signal at C1108? Check filter between C1108 & C2308. Check tuning voltage at R2309 No Check Harmonic Filter J1 and Antenna Switch D103,D104,L1514 Is tuning voltage OK? No Check U517 Yes Check varactor filter D2301, D2304 3-12 6.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for DC Supply (1 of 2) Since the failure of a critical voltage supply might cause the radio to automatically power down, supply voltages should first be probed with a multimeter. If all the board voltages are absent, then the voltage test point should be retested using a rising-edge-triggered oscilloscope. If the voltage is still absent, then another voltage should be tested using the oscilloscope. If that voltage is present, then the original voltage supply in question is defective and requires investigation of associated circuitry. 5V Check VDC on C5006 Go to 3V Replace U503 Yes Yes V=5V ? 9v 1 GHz Audio Response: (from 6 dB/ oct. Pre-Emphasis, 300 to 3000Hz) TIA603 and CEPT Tx Audio Distortion < 3% Modulation Limiting: ±2.5 kHz @ 12.5 kHz ±4.0 kHz @ 20 kHz ±5.0 kHz @ 25 kHz FM Hum and Noise: -35 dB@12.5 kHz -40 dB@25 kHz Receiver Specification Sensitivity (12 dB SINAD): UHF2 0.35 µV @ 12.5 kHz 0.3 µV @ 25 kHz Intermodulation: 60 dB@12.5 kHz 70 dB@25 kHz Adjacent Channel Selectivity: 60 dB @ 12.5 kHz 70 dB @ 25 kHz Spurious Response 70 dB Rated Audio Power 4 W (typ.) Internal 7.5 W @ 5 % External Audio Distortion <5% Hum and Noise: -35 dB @ 12.5 kHz -40 dB @ 25 kHz Audio Response TIA603 and CEPT Conducted Spurious Emission per FCC Part 15: -57 dBm <1 Ghz -47 dBm >1 Ghz Specifications subject to change without notice. All electrical specifications and methods refer to EIA/TIA 603 standards. 1-4 MODEL CHART AND TECHNICAL SPECIFICATIONS THIS PAGE INTENTIONALLY LEFT BLANK Chapter 2 THEORY OF OPERATION 1.0 Introduction This Chapter provides a detailed theory of operation for the UHF circuits in the radio. Details of the theory of operation and trouble shooting for the the associated Controller circuits are included in this Section of the manual. 2.0 UHF (438-470MHz) Receiver 2.1 Receiver Front-End The received signal is applied to the radio’s antenna input connector and routed through the harmonic filter and antenna switch. The insertion loss of the harmonic filter/antenna switch is less than 1 dB. The signal is routed to the first filter (3-pole), which has an insertion loss of 2 dB typically. The output of the filter is matched to the base of the LNA (Q303) that provides a 16 dB gain and a noise figure of better than 2 dB. Current source Q301 is used to maintain the collector current of Q303. Diode CR301 protects Q303 by clamping excessive input signals. Q303 output is applied to the second filter (4-pole) which has an insertion loss of 1.5 dB. In Distance mode, Q304 turns on and causes D305 to conduct, thus bypassing C322 and R337. In Local mode, the signal is routed through C322 and R337, thus inserting 7 dB attenuation. Since the attenuator is located after the RF amplifier, the receiver sensitivity is reduced only by 6 dB, while the overall third order input intercept is raised. The first mixer is a passive, double-balanced type, consisting of T300, T301 and U302. This mixer provides all of the necessary rejection of the half-IF spurious response. Low-side injection at +10 dBm is delivered to the first mixer. The mixer output is then connected to a duplex network which matches its output to the XTAL filter input (FL300) at the IF frequency of 44.85 MHz. The duplex network terminates into a 50 ohm resistor (R340) at all other frequencies. Antenna Front Filter 12.5kHzFilter 12.5kHzFilter LNA Second Filter Mixer 4- Pole Xtal Filter IF Amp First LO 25kHzFilter 25kHzFilter IFIC 2nd LO Xtal Osc Phase Shift Element Controller Figure 2-1 UHF Receiver Block Diagram 2-2 THEORY OF OPERATION 2.2 Receiver Back End The IF signal from the crystal filter enters the IF amplifier which provides 20 dB of gain and feeds the IF IC at pin 1. The first IF signal at 44.85 MHz mixes with the second local oscillator (LO) at 44.395 MHz to produce the second IF at 455 kHz. The second LO uses the external crystal Y301. The second IF signal is amplified and filtered by two external ceramic filters (FL303/FL302 for 12.5KHz channel spacing and FL304/FL301 for 25KHz channel spacing). The IF IC demodulates the signal by means of a quadrature detector and feeds the detected audio (via pin 7) to the audio processing circuits. At IF IC pin 5, an RSSI signal is available with a dynamic range of 70 dB. 3.0 UHF Transmitter Power Amplifier (438-470 MHz) The radio’s 40W PA is a three-stage amplifier used to amplify the output from the VCOBIC to the radio transmit level. All three stages utilize LDMOS technology. The gain of the first stage (U101) is adjustable and controlled by pin 7 of U103-2 via U103-3. It is followed by an LDMOS stage Q105 and LDMOS final stage Q100. Pin Diode Antenna Switch From VCO Controlled Stage PA Driver PA-Final Stage Antenna Harmonic Filter RF Jack Coupler Bias Forward A S FI C _C M P SPI BUS PA PWR SET L oo p C ont r ol le r U 103 - 2 Temperature Sense Figure 2-2 UHF Transmitter Block Diagram Devices U101, Q105 and Q100 are surface mounted. Q100 is screwed down to the chassis to ensure good thermal contact. This scheme also ensures sufficient thermal contact between driver and chassis. 3.1 First Power Controller Stage The first stage (U101) is a 24dB gain integrated circuit containing two LDMOS FET amplifier stages. It amplifies the RF signal from the VCO (TX_INJ). The output power of stage U101 is controlled by a DC voltage applied to pin 1 from the op-amp U103-3, pin 8. The control voltage simultaneously varies the bias of two FET stages within U101. This biasing point determines the overall gain of U101 and therefore its output drive level to Q105, which in turn controls the output power of the UHF Transmitter Power Amplifier (438-470 MHz) 2-3 PA.Op-amp U103-3 monitors the drain current of U101 via resistor R122 and adjusts the bias voltage of U101. In receive mode, the DC voltage from RX_EN line turns on Q101, which in turn switches off the biasing voltage to U101. 3.2 Power Controlled Driver Stage The next stage is an LDMOS device (Q105) which provides a gain of 12dB. This device requires a positive gate bias and a quiescent current flow for proper operation.The voltage of the PA_CURRENT is set in transmit mode by ASFIC (U504 pin 5) and fed to the gate of Q105 via resistive network R186, R187. This bias voltage is tuned in the factory. If the transistor is replaced, the bias voltage must be tuned using Global Tuner. Care must be taken so that the transistor is not tuned exceeding the allowed bias voltage. This device directly drains current from B+ via L122. 3.3 Final Stage The final stage is an LDMOS device (Q100) providing a gain of 12dB. This device also requires a positive gate bias and a quiescent current flow for proper operation. The voltage of the line PA_BIAS is set in transmit mode by ASFIC (U504 pin 4) and fed to the gate of Q100 via the resistive network R134, R131. This bias voltage is tuned in the factory. If the transistor is replaced, the bias voltage must be tuned using the Global Tuner. Care must be taken not to damage the device by exceeding the maximum allowed bias voltage. The device’s drain current is drawn directly from the radio’s DC supply voltage input, B+, via L117, L115, L124 and L125. A matching network consisting of C1005, C1017, C1004, C1009, C1008, C1007, C1274, C1279, C1275, C1276, C1277, C1278, C1021, C1280, C1013, L126, L127 and two striplines, transforms the impedance to 50 ohms and feeds the directional coupler. 3.4 Directional Coupler The directional Coupler is a microstrip printed circuit, which couples a small amount of the forward power of the RF power from Q100. Coupled power is rectified by diode D105 to produce a proportional DC voltage; and the resulting DC voltage is routed to the power control section to ensure that the forward power out of the radio is held to a constant value. 3.5 Antenna Switch The antenna switch utilizes the existing dc feed (B+) to the last stage device (Q100). The basic operation is to have both PIN diodes (D103, D104) turned on during key-up by forward biasing them. This is achieved by pulling down the voltage at the cathode end of D104 to around 12.4V (0.7V drop across each diode). The current through the diodes needs to be set around 100 mA to fully open the transmit path through resistor R108. Q106 is a current source controlled by Q103 which is turned on in Tx mode by TX_EN. VR102 ensures that the voltage at resistor R107 never exceeds 5.6V. 2-4 3.6 THEORY OF OPERATION Harmonic Filter Inductors L111, L113 and L128 along with capacitors C1011, C1023, C1020, C1016, C1025 and C1026 form a low-pass filter to attenuate harmonic energy coming from the transmitter. Resistor R150 along with L130 drains any electrostatic charges that might otherwise build up on the antenna. The harmonic filter also prevents high level RF signals above the receiver passband from reaching the receiver circuits to improve spurious response rejection. 3.7 Power Control The output power is regulated by using a forward power detection control loop. A directional coupler samples a portion of the forward and reflected RF power. The forward sampled RF is rectified by diode D105, and the resulting DC voltage is routed to the operational amplifier U100. The error output current is then routed to an integrator, and converted into the control voltage. This voltage controls the bias of the pre-driver (U101) stage. The output power level is set by PWR_SET at ASFIC (U504 pin 6) which acts as the reference for forward power control loop. The reflected coupled power is rectified by diode D107,The resulting DC voltage is amplified by an operational amplifier U100 and routed to the summing junction. This detector protects the final stage Q100 from reflected power by increasing the error current. The temperature sensor protects the final stage Q100 from overheating by increasing the error current. A thermistor RT100 measures the final stage Q100 temperature. The voltage divider output is routed to an operational amplifier U103 and then goes to the summing junction. The Zener Diode VR101 keeps the loop control voltage below 5.6V and eliminates the DC current from the 9.3 regulator U501. One local loop for the Pre Driver (U101) is used in order to stabilize the current for each stage. In Rx mode, the two transistors Q101 and Q102 go to saturation and shut down the transmitter by applying ground to the Pre Driver U101. 4.0 UHF (438-470MHz) Frequency Synthesizer The synthesizer consists of a reference oscillator (Y201), low voltage Fractional-N (LVFRAC-N) synthesizer (U200), and a voltage controlled oscillator (VCO) (U201). 4.1 Reference Oscillator The reference oscillator is a crystal (Y201) controlled Colpitts oscillator and has a frequency of 16.8MHz. The oscillator transistor and start-up circuit are located in the LVFRAC-N (U200) while the oscillator feedback capacitors, crystal, and tuning varactors are external. An analog-to-digital (A/D) converter internal to the LVFRAC-N (U200) and controlled by the microprocessor via SPI sets the voltage at the warp output of U200 pin 25. This sets the frequency of the oscillator. Consequently, the output of the crystal Y201 is applied to U200 pin 23. The method of temperature compensation is to apply an inverse Bechmann voltage curve, which matches the crystal’s Bechmann curve to a varactor that constantly shifts the oscillator back on frequency. The crystal vendor characterizes the crystal over a specified temperature range and codes this information into a bar code that is printed on the crystal package. In production, this crystal code is read via a 2-dimensional bar code reader and the parameters are saved. This oscillator is temperature compensated to an accuracy of +/-2.5 PPM from -30 to 60 degrees C. The temperature compensation scheme is implemented by an algorithm that uses five crystal UHF (438-470MHz) Frequency Synthesizer 2-5 parameters (four characterize the inverse Bechmann voltage curve and one for frequency accuracy of the reference oscillator at 25 degrees C). This algorithm is implemented by the LVFRAC-N (U200) at the power up of the radio. TCXO Y200, along with its corresponding circuitry R204, R205, R210, and C2053, are not placed as the temperature compensated crystal proved to be reliable. 4.2 Fractional-N Synthesizer The LVFRAC-N U200 consists of a pre-scaler, programmable loop divider, control divider logic, phase detector, charge pump, A/D converter for low frequency digital modulation, balanced attenuator used to balance the high and low frequency analog modulation, 13V positive voltage multiplier, serial interface for control, and a super filter for the regulated 5 volts. DATA (U403 PIN 100) CLOCK (U403 PIN 1) CSX (U403 PIN 2) MOD IN (U501 PIN 40) +5V (U503 PIN 1) +5V (U503 PIN 1) 7 8 9 10 13, 30 5, 20, 34, 36 REFERENCE OSCILLATOR 23 24 VOLTAGE MULTIPLIER FREFOUT CLK GND CEX MODIN VCC, DC5V IOUT IADAPT VDD, DC5V MODOUT XTAL1 U200 XTAL2 FRACTIONAL-N SYNTHESIZER 25 WARP 32 PREIN 47 LOCK DATA LOW VOLTAGE VCP VMULT2 14 15 48 43 45 LOOP FILTER STEERING LINE 41 AUX3 2 AUX1 BIAS2 FREF (U504 PIN 34) 6, 22, 33, 44 3 1 (NU) BIAS1 LOCK (U403 PIN 56) 19 AUX4 AUX2 SFOUT VMULT1 4 VCO Bias LO RF INJECTION TRB VOLTAGE 28 FILTERED 5V CONTROLLED OSCILLATOR 40 TX RF INJECTION (1ST STAGE OF PA) 39 BWSELECT To IF Section PRESCALER IN Figure 2-3 UHF Synthesizer Block Diagram A voltage of 5V applied to the super filter input (U200, pin 30) supplies an output voltage of 4.5Vdc (VSF) at U200, pin 28. This supplies 4.5 V to the VCO Buffer IC U201. To generate a high voltage to supply the phase detector (charge pump) output stage at pin VCP (U200, pin 47) while using a low voltage 3.3Vdc supply, a 13V positive voltage multiplier is used (D200, D201, and capacitors C2024, 2025, 2026, 2055, 2027, 2001). Output lock (U200, pin 4) provides information about the lock status of the synthesizer loop. A high level at this output indicates a stable loop. A 16.8 MHz reference frequency is provided at U200, pin 19. 2-6 THEORY OF OPERATION 4.3 Voltage Controlled Oscillator (VCO) The Voltage Controlled Oscillator (VCO) consists of the VCO/Buffer IC (VCOBIC, U201), the TX and RX tank circuits, the external RX buffer stages, and the modulation circuitry. AUX3 (U200 Pin 2) Prescaler Out TRB IN Pin 20 Rx-SW Pin7 Tx-SW Pin13 (U200 Pin 28) Pin 19 U200 Pin 32 Pin 12 TX/RX/BS Switching Network Vcc-Superfilter Pin3 LO RF INJECTION Presc U201 VCOBIC Q200 Buffers Low Pass Filter Collector/RF in Steer Line Voltage (VCTRL) Pin4 RX Tank RX VCO Circuit TX VCO Circuit Rx Active Bias Pin5 Pin6 TX Tank RX RX Pin8 Pin14 TX Tx Active Bias Pin16 Pin15 TX Pin10 Vcc-Logic TX RF Injection Attenuator Vsens Circuit Pin18 (U200 Pin28) VCC Buffers Pin2 Pin1 Rx-I adjust Tx-I adjust Pins 9,11,17 (U200 Pin 28) Figure 2-4 UHF VCO Block Diagram The VCOBIC together with the LVFRAC-N (U200) generate the required frequencies in both transmit and receive modes. The TRB line (U201, pin 19) determines which VCO and buffer is enabled (high being TX output at pin 10, low being RX output at pin 8). A sample of the signal from the enabled output is routed from U201, pin 12 (PRESC_OUT), via a low pass filter to U200, pin 32 (PREIN). A steering line voltage between 3.0V and 10.0V at varactor D204 tunes the TX VCO through the frequency range of 438-470MHz, and at D203 tunes the RX VCO through the frequency range of 393.15-425.15MHz. The external RX amplifier is used to increase the output from U201, pin 8 from 3-4 dBm to the required 10dBm for proper mixer operation. In TX mode, the modulation signal from the LVFRAC-N (U200, pin 41) is applied to the VCO by way of the modulation circuit D205, R212, R211, C2073. UHF (438-470MHz) Frequency Synthesizer 4.4 2-7 Synthesizer Operation The synthesizer consists of a low voltage FRAC-N IC (LVFRAC-N), reference oscillator, charge pump circuits, loop filter circuit, and DC supply. The output signal (PRESC_OUT) of the VCOBIC (U201, pin 12) is fed to the PREIN, pin 32 of U200 via a low pass filter which attenuates harmonics and provides a correct input level to the LVFRAC-N in order to close the synthesizer loop. The pre-scaler in the synthesizer (U200) is a dual modulus pre-scaler with selectable divider ratios. The divider ratio of the pre-scaler is controlled by the loop divider, which in turn receives its inputs via the SPI. The output of the pre-scaler is applied to the loop divider. The output of the loop divider is connected to the phase detector, which compares the loop divider’s output signal with the reference signal. The reference signal is generated by dividing down the signal of the reference oscillator (Y201). The output signal of the phase detector is a pulsed dc signal that is routed to the charge pump. The charge pump outputs a current from U200, pin 43 (IOUT). The loop filter (consisting of R224, R217, R234, C2074, C2078, C2028, and L205) transforms this current into a voltage that is applied the varactor diodes D203 and D204 for RX and TX respectively. The output frequency is determined by this control voltage. The current can be set to a value fixed in the LVFRAC-N or to a value determined by the currents flowing into BIAS 1 (U200, pin 40) or BIAS 2 (U200, pin 39). The currents are set by the value of R200 or R206 respectively. The selection of the three different bias sources is done by software programming. To modulate the synthesizer loop, a two-spot modulation method is utilized via the MODIN (U200, pin 10) input of the LVFRAC-N. The audio signal is applied to both the A/D converter (low frequency path) and the balance attenuator (high frequency path). The A/D converter converts the low frequency analog modulating signal into a digital code which is applied to the loop divider, thereby causing the carrier to deviate. The balance attenuator is used to adjust the VCO’s deviation sensitivity to high frequency modulating signals. The output of the balance attenuator is presented at the MODOUT port of the LVFRAC-N (U200,pin 41) and connected to the VCO modulation varactor D205. 2-8 5.0 THEORY OF OPERATION Controller Theory of Operation This section provides a detailed theory of operation for the radio and its components. The main radio is a single-board design, consisting of the transmitter, receiver, and controller circuits. A control head is connected by an extension cable. The control head contains LED indicators, a microphone connector, buttons, and speaker. In addition to the power cable and antenna cable, an accessory cable can be attached to a connector on the rear of the radio. The accessory cable enables you to connect accessories to the radio, such as an external speaker, emergency switch, foot-operated PTT, and ignition sensing, etc. External Microphone To Synthesizer Mod Out 16.8 MHz Reference Clock from Synthesizer Audio/Signaling Architecture Disc Audio ASFIC_CMP . Internal Microphone External Speaker Audio PA Internal Speaker µP Clock SPI To RF Section Digital Architecture SCI to Accessory & Control Head Connector RAM EEPROM 3.3V Regulator HC11FL0 FLASH Figure 2-5 Controller Block Diagram 5.1 Radio Power Distribution Voltage distribution is provided by five separate devices: • U514 P-cH FET - Batt + (Ext_SWB+) • U501 LM2941T - 9.3V • U503 LP2951CM - 5V • U508 MC 33269DTRK - 3.3V • U510 LP2986ILDX - 3.3V Digital Handset Controller Theory of Operation 2-9 The DC voltage applied to connector P2 supplies power directly to the following circuitry: • Electronic on/off control • RF power amplifier • 12 volts P-cH FET -U514 • 9.3 volt regulator • Audio PA Ignition Auto On/Off Switch Control B+ Control Head RF_PA, 8.5A Audio_PA Mic Connector Ferrite Bit Filt_B+ Antenna Switch Power Control 500mA FET P-CH On/Off Control SW_Filt_B+ 10.9-16.3V 0.9A Status LEDs 7_Seg 7_Seg DOT Bed to 7-Seg Back light Shift Reg Acces Conn Audio PA_Soutdown Power Loop Op_Amp 9.3V 65mA U501 9.3V Regulator Keypad Mic Bias 9V, 5mA 0.85A Reset 9.3V 45mA On/Off Control U503 5V RF Regulator 500mA Rx_Amp PA_Pre-driver PA Driver 3.2V 72mA 45mA LVFRAC_N IF_Amp 9.3V 75mA 9.3V 162mA U508 3.3V RF Reg 50mA 25mA ASFIC_CMP IFIC RX Cct U510 3.3V D Reg 90mA micro P RAM Flash EEPROM Figure 2-6 DC Power Distribution Block Diagram Regulator U501 is used to generate the 9.3 volts required by some audio circuits, the RF circuitry and power control circuitry. Input and output capacitors are used to reduce high frequency noise. Resistors R5001 / R5081 set the output voltage of the regulator. This regulator output is electronically enabled by a 0 volt signal on pin 2. Q502, Q505 and R5038 are used to disable the regulator when the radio is turned off. Voltage regulator U510 provides 3.3 volts for the digital circuitry. Operating voltage is from the regulated 9.3V supply. Input and output capacitors are used to reduce high frequency noise and provide proper operation during battery transients. U510 provides a reset output that goes to 0 volts if the regulator output goes below 3.1 volts. This is used to reset the controller to prevent improper operation. Voltage regulator U508 provides 3.3V for the RF circuits and ASFIC_CMP. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. 2-10 THEORY OF OPERATION Voltage regulator U503 provides 5V for the RF circuits. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. VSTBY is used only for GM3689 5-tone radios. The voltage VSTBY, which is derived directly from the supply voltage by components R5103 and VR502, is used to buffer the internal RAM. Capacitor C5120 allows the battery voltage to be disconnected for a couple of seconds without losing RAM parameters. Dual diode D501 prevents radio circuitry from discharging this capacitor. When the supply voltage is applied to the radio, C5120 is charged via R5103 and D501. 5.2 Protection Devices Diode VR500 acts as protection against ESD, wrong polarity of the supply voltage, and load dump. VR692 - VR699 are for ESD protection. 5.3 Automatic On/Off The radio can be switched ON in any one of the following three ways: 5.3.1 • On/Off switch. (No Ignition Mode) • Ignition and On/Off switch (Ignition Mode) • Emergency No Ignition Mode When the radio is connected to the car battery for the first time, Q500 will be in saturation, Q503 will cut-off, Filt_B+ will pass through R5073, D500, and S5010-pin 6 (On/Off switch). When S5010 is ON, Filt_B+ will pass through S5010-pin5, D511, R5069, R5037 and base of Q505 and move Q505 into saturation. This pulls U501-pin2 through R5038, D502 to 0.2V and turns On U514 and U501 9.3V regulator which supplies voltage to all other regulators and consequently turns the radio on, When U504 (ASFIC_CMP) gets 3.3V, GCB2 goes to 3.3V and holds Q505 in saturation, for soft turn off. 5.3.2 Ignition Mode When ignition is connected for the first time, it will force high current through Q500 collector, This will move Q500 out of saturation and consequently Q503 will cut-off. S5010 pin 6 will get ignition voltage through R601 (for load dump), R610, (R610 & C678 are for ESD protection), VR501, R5074, and D500. When S5010 is ON, Filt_B+ passes through S5010-pin 5, D511, R5069, R5037 and base of Q505 and inserts Q505 into saturation. This pulls U501-pin 2 through R5038, D502 to 0.2V and turns on U514 and U501 9.3V regulator which supply voltage to all other regulators and turns the radio on, When U504 (ASFIC_CMP) get 3.3V supply, GCB2 goes to 3.3V and holds Q505 in saturation state to allow soft turn off, When ignition is off Q500, Q503 will stay at the same state so S5010 pin 6 will get 0V from Ignition, Q504 goes from Sat to Cut, ONOFF_SENSE goes to 3.3V and it indicates to the radio to soft turn itself by changing GCB2 to ‘0’ after de registration if necessary. Controller Theory of Operation 5.3.3 2-11 Emergency Mode The emergency switch (P1 pin 9), when engaged, grounds the base of Q506 via EMERGENCY _ACCES_CONN. This switches Q506 to off and consequently resistor R5020 pulls the collector of Q506 and the base of Q506 to levels above 2 volts. Transistor Q502 switches on and pulls U501 pin2 to ground level, thus turning ON the radio. When the emergency switch is released R5030 pulls the base of Q506 up to 0.6 volts. This causes the collector of transistor Q506 to go low (0.2V), thereby switching Q502 to off. While the radio is switched on, the µP monitors the voltage at the emergency input on the accessory connector via U403-pin 62. Three different conditions are distinguished: no emergency kit is connected, emergency kit connected (unpressed), and emergency press. If no emergency switch is connected or the connection to the emergency switch is broken, the resistive divider R5030 / R5049 will set the voltage to about 3.14 volts (indicates no emergency kit found via EMERGENCY_SENSE line). If an emergency switch is connected, a resistor to ground within the emergency switch will reduce the voltage on EMERGENCY _SENSE line, and indicate to the µP that the emergency switch is operational. An engaged emergency switch pulls line EMERGENCY _SENSE line to ground level. Diode VR503 limits the voltage to protect the µP input. While EMERGENCY _ACCES_CONN is low, the µP starts execution, reads that the emergency input is active through the voltage level of µP pin 64, and sets the DC POWER ON output of the ASFIC CMP pin 13 to a logic high. This high will keep Q505 in saturation for soft turn off. 5.4 Microprocessor Clock Synthesiser The clock source for the µP system is generated by the ASFIC CMP (U504). Upon power-up the synthesizer IC (FRAC-N) generates a 16.8 MHz waveform that is routed from the RF section to the ASFIC CMP pin 34. For the main board controller the ASFIC CMP uses 16.8 MHz as a reference input clock signal for its internal synthesizer. The ASFIC CMP, in addition to audio circuitry, has a programmable synthesizer which can generate a synthesized signal ranging from 1200Hz to 32.769MHz in 1200Hz steps. When power is first applied, the ASFIC CMP will generate its default 3.6864MHz CMOS square wave UP CLK (on U504 pin 28) and this is routed to the µP (U403 pin 90). After the µP starts operation, it reprograms the ASFIC CMP clock synthesizer to a higher UP CLK frequency (usually 7.3728 or 14.7456 MHz) and continues operation. The ASFIC CMP may be reprogrammed to change the clock synthesizer frequencies at various times depending on the software features that are executing. In addition, the clock frequency of the synthesizer is changed in small amounts if there is a possibility of harmonics of the clock source interfering with the desired radio receive frequency. The ASFIC CMP synthesizer loop uses C5025, C5024 and R5033 to set the switching time and jitter of the clock output. If the synthesizer cannot generate the required clock frequency it will switch back to its default 3.6864MHz output. Because the ASFIC CMP synthesizer and the µP system will not operate without the 16.8 MHz reference clock it (and the voltage regulators) should be checked first when debugging the system. 2-12 5.5 THEORY OF OPERATION Serial Peripheral Interface (SPI) The µP communicates to many of the IC’s through its SPI port. This port consists of SPI TRANSMIT DATA (MOSI) (U403-pin100), SPI RECEIVE DATA (MISO) (U403-pin 99), SPI CLK (U0403-pin1) and chip select lines going to the various IC’s, connected on the SPI PORT (BUS). This BUS is a synchronous bus, in that the timing clock signal CLK is sent while SPI data (SPI TRANSMIT DATA or SPI RECEIVE DATA) is sent. Therefore, whenever there is activity on either SPI TRANSMIT DATA or SPI RECEIVE DATA there should be a uniform signal on CLK. The SPI TRANSMIT DATA is used to send serial from a µP to a device, and SPI RECEIVE DATA is used to send data from a device to a µP. There are two IC’s on the SPI BUS, ASFIC CMP (U504 pin 22)), and EEPROM (U400). In the RF sections there is one IC on the SPI BUS, the FRAC-N Synthesizer. The chip select line CSX from U403 pin 2 is shared by the ASFIC CMP and FRAC-N Synthesizer. Each of these IC’s check the SPI data and when the sent address information matches the IC’s address, the following data is processed. When the µP needs to program any of these Is it brings the chip select line CSX to a logic “0” and then sends the proper data and clock signals. The amount of data sent to the various IC’s are different; e.g., the ASFIC CMP can receive up to 19 bytes (152 bits). After the data has been sent the chip select line is returned to logic “1”. 5.6 SBEP Serial Interface The SBEP serial interface allows the radio to communicate with the Customer Programming Software (CPS), or the Universal Tuner via the Radio Interface Box (RIB) or the cable with internal RIB. This interface connects to the SCI pin via control head connector (J2-pin 17) and to the accessory connector P1-6 and comprises BUS+. The line is bi-directional, meaning that either the radio or the RIB can drive the line. The µP sends serial data and it reads serial data via pin 97. Whenever the µP detects activity on the BUS+ line, it starts communication. 5.7 General Purpose Input/Output The controller provides six general purpose lines (PROG I/O) available on the accessory connector P1 to interface to external options. Lines PROG IN 3 and 6 are inputs, PROG OUT 4 is an output and PROG IN OUT 8, 12 and 14 are bi-directional. The software and the hardware configuration of the radio model define the function of each port. • PROG IN 3 can be used as external PTT input, or others, set by the CPS. The µP reads this port via pin 72 and Q412. • PROG OUT 4 can be used as external alarm output, set by the CPS. Transistor Q401 is controlled by the µP (U403 pin 55) • PROG IN 6 can be used as normal input, set by the CPS. The µP reads this port via pin 73 and Q411. This pin is also used to communicate with the RIB if resistor R421 is placed. • DIG IN OUT 8,12,14 are bi-directional and use the same circuit configuration. Each port uses an output Q416, Q404, Q405 controlled by µP pins 52, 53, 54. The input ports are read through µP pins 74, 76, 77; using Q409, Q410, Q411 Controller Theory of Operation 5.8 2-13 Normal Microprocessor Operation For this radio, the µP is configured to operate in one of two modes, expanded and bootstrap. In expanded mode the µP uses external memory devices to operate, whereas in bootstrap operation the µP uses only its internal memory. In normal operation of the radio the µP is operating in expanded mode as described below. During normal operation, the µP (U403) is operating in expanded mode and has access to 3 external memory devices; U400 (EEPROM), U402 (SRAM), U404 (Flash). Also, within the µP there are 3 Kilobytes of internal RAM, as well as logic to select external memory devices. The external EEPROM (U400) space contains the information in the radio which is customer specific, referred to as the codeplug. This information consists of items such as: 1) what band the radio operates in, 2) what frequencies are assigned to what channel, and 3) tuning information. The external SRAM (U402) as well as the µP’s own internal RAM space are used for temporary calculations required by the software during execution. All of the data stored in both of these locations is lost when the radio powers off. The µP provides an address bus of 16 address lines (ADDR 0 - ADDR 15), and a data bus of 8 data lines (DATA 0 - DATA 7). There are also 3 control lines; CSPROG (U403-38) to chip select U404-pin 30 (FLASH), CSGP2 (U403-pin 41) to chip select U404-pin 20 (SRAM) and PG7_R_W (U403-pin 4) to select whether to read or to write. The external EEPROM (U400-pin1). When the µP is functioning normally, the address and data lines should be toggling at CMOS logic levels. Specifically, the logic high levels should be between 3.1 and 3.3V, and the logic low levels should be between 0 and 0.2V. No other intermediate levels should be observed, and the rise and fall times should be <30ns. The low-order address lines (ADDR 0 - ADDR 7) and the data lines (DATA 0-DATA 7) should be toggling at a high rate, e.g., you should set your oscilloscope sweep to 1us/div. or faster to observe individual pulses. High speed CMOS transitions should also be observed on the µP control lines. On the µP the lines XIRQ (U403-pin 48), MODA LIR (U403-pin 58), MODB VSTPY (U403-pin 57) and RESET (U403-pin 94) should be high at all times during normal operation. Whenever a data or address line becomes open or shorted to an adjacent line, a common symptom is that the RESET line goes low periodically, with the period being in the order of 20ms. In the case of shorted lines you may also detect the line periodically at an intermediate level, i.e. around 2.5V when two shorted lines attempt to drive to opposite rails. The MODA LIR (U403-pin 58) and MODB VSTPY (U403-pin 57) inputs to the µP must be at a logic “1” for it to start executing correctly. After the µP starts execution it will periodically pulse these lines to determine the desired operating mode. While the Central Processing Unit (CPU) is running, MODA LIR is an open-drain CMOS output which goes low whenever the µP begins a new instruction. An instruction typically requires 2-4 external bus cycles, or memory fetches. There are eight analog-to-digital coverter ports (A/D) on U403 labelled within the device block as PEO-PE7. These lines sense the voltage level ranging from 0 to 3.3V of the input line and convert that level to a number ranging from 0 to 255 which is read by the software to take appropriate action. 2-14 5.9 THEORY OF OPERATION Static Random Access Memory (SRAM) The SRAM (U402) contains temporary radio calculations or parameters that can change very frequently, and which are generated and stored by the software during its normal operation. The information is lost when the radio is turned off. The device allows an unlimited number of write cycles. SRAM accesses are indicated by the CS signal U402 (which comes from U403-CSGP2) going low. U402 is commonly referred to as the external RAM as opposed to the internal RAM which is the 3 Kilobytes of RAM which is part of the 68HC11FL0. Both RAM spaces serve the purpose. However, the internal RAM is used for the calculated values which are accessed most often. Capacitor C402 and C411 serves to filter out any AC noise which may ride on +3.3 V at U402 6.0 Control Board Audio and Signalling Circuits 6.1 Audio Signalling Filter IC and Compander (ASFIC CMP) The ASFIC CMP (U504) used in the controller has the following four functions: 1. RX/TX audio shaping, i.e. filtering, amplification, attenuation 2. RX/TX signaling, PL/DPL/HST/MDC 3. Squelch detection 4. µP clock signal generation The ASFIC CMP is programmable through the SPI BUS (U504 pins-20/21/22), normally receiving 19 bytes. This programming sets up various paths within the ASFIC CMP to route audio and/or signaling signals through the appropriate filtering, gain and attenuator blocks. The ASFIC CMP also has 6 General Control Bits GCB0-5 which are CMOS level outputs and used for the following: • GCBO - BW Select • GCBI - switches the audio PA On/Off • GCB2 - DC Power On switches the voltage regulator (and the radio) on and off • GCB3 - Control on MUX U509 pin 9 to select between Low Cost Mic path to STD Mic Path • GCB4 - Control on MUX U509 pin 11 to select between Flat RX path to filtered RX path on the accessory connector. • GCB5 - Control on MUX U509 pin 10 to select between Flat TX path mute and Flat TX path Transmit Audio Circuits 7.0 2-15 Transmit Audio Circuits J2 24kOhms U509 15 MIC 46 35 P1 48 2 FLAT TX AUDIO MIC INT GCB3 MIC EXT U509 5 36 TX RTN MUX CONTROL HEAD CONNECTOR EXT MIC 44 TX SND 42 MUX AUX TX ACCESSORY CONNECTOR FILTERS AND PREEMPHASIS MIC ASFIC_CMP IN U504 LIMITER HS SUMMER SPLATTER FILTER LS SUMMER 38 GCB5 FLAT TX AUDIO MUTE VCO ATN ATTENUATOR MOD IN 40 TO RF SECTION (SYNTHESIZER) Figure 2-7 Transmit Audio Paths 7.1 Microphone Input Path The radio supports 2 distinct microphone paths known as internal (from control head J2-15) and external mic (from accessory connector P1-2) and an auxiliary path (FLAT TX AUDIO, from accessory connector P1-5). The microphones used for the radio require a DC biasing voltage provided by a resistive network. The two microphone audio input paths enter the ASFIC CMP at U504-pin 48 (external mic) and U504-pin 46 (internal mic). The microphone is plugged into the radio control head and connected to the audio DC via J2-pin 15. The signal is then routed via C5045 to MUX U509 that select between two paths with different gain to support Low Cost Mic (Mic with out amplifier in it) and Standard Mic. 7.1.1 Low Cost Microphone Hook Pin is shorted to Pin 1(9.3V) inside the Low Cost Mic, This routes 9.3V to R429, and creates 2.6V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 = ‘0’. The audio signal is routed from C5045 via U509-5 (Z0), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int. mic (C5046 100nF creates a159Hz pole with U504- 46 int mic impedance of 16Kohm). 2-16 7.1.2 THEORY OF OPERATION Standard Microphone Hook Pin is shorted to the hook mic inside the standard Mic, If the mic is out off hook, 3.3V is routed to R429 via R458, D401, and it create 0.7V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 =‘1’. The audio signal is routed from C5045 via U509-3 (Z1), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int mic (C5046 100nF create a159Hz pole with U504- 46 int mic impedance of 16Kohm). 9.3VDC is routed via R5077, R5075 to J2-15, It create 4.65V with Mic Impedance. C5010 supplies AC Ground to create AC impedance of 510 Ohms via R5075. and Filter 9.3V DC mic bias supply. Note: The audio signal at U504-pin 46 should be approximately 12mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The external microphone signal enters the radio on accessory connector P1 pin 2 and is routed via line EXT MIC to R5054. R5078 and R5076 provide the 9.3Vdc bias. Resistive divider R5054/ R5070 divide the input signal by 5.5 and provide input protection for the CMOS amplifier input. R5076 and C5009 provide a 510 ohm AC path to ground that sets the input impedance for the microphone and determines the gain based on the emitter resistor in the microphone’s amplifier circuit. C5047 serves as a DC blocking capacitor. The audio signal at U504-pin 48 should be approximately 14mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The FLAT TX AUDIO signal from accessory connector P1-pin 5 is fed to the ASFIC CMP (U504 pin 42 through U509 pin 2 to U509 pin 15 via U506 OP-AMP circuit and C5057. The ASFIC has an internal AGC that can control the gain in the mic audio path. The AGC can be disabled / enabled by the µP. Another feature that can be enabled or disabled in the ASFIC is the VOX. This circuit, along with Capacitor C5023 at U504-pin 7, provides a DC voltage that can allow the µP to detect microphone audio. The ASFIC can also be programmed to route the microphone audio to the speaker for public address operation. 7.2 PTT Sensing and TX Audio Processing Internal microphone PTT is sensed by µP U403 pin 71. Radio transmits when this pin is “0” and selects inside the ASFIC_ CMP U504 internal Mic path. When the internal Mic PTT is “0” then external Mic PTT is grounded via D402. External Mic PTT is sensed by U403 pin 72 via Q412 circuits. The radio transmits when this pin is “0” and selects inside the ASFIC _CMP U504 External Mic path. Inside the ASFIC CMP, the mic audio is filtered to eliminate frequency components outside the 3003000Hz voice band, and pre-emphasized if pre-emphasis is enabled. The signal is then limited to prevent the transmitter from over deviating. The limited mic audio is then routed through a summer, which is used to add in signaling data, and then to a splatter filter to eliminate high frequency spectral components that could be generated by the limiter. The audio is then routed to an attenuator, which is tuned in the factory or the field to set the proper amount of FM deviation. The TX audio emerges from the ASFIC CMP at U504-pin 40 MOD IN, at which point it is routed to the RF section. Transmit Signalling Circuits 8.0 2-17 Transmit Signalling Circuits HS SUMMER 44 MICRO CONTROLLER U403 19 HIGH SPEED CLOCK IN (HSIO) DTMF ENCODER 82 SPI BUS SPLATTER FILTER ASFIC_CMP U504 85 80 5-3-2 STATE ENCODER 18 LOW SPEED CLOCK IN (LSIO) PL ENCODER LS SUMMER ATTENUATOR 40 MOD IN TO RF SECTION (SYNTHESIZER) Figure 2-8 Transmit Signalling Path From a hardware point of view, there are 3 types of signaling: • Sub-audible data (PL / DPL / Connect Tone) that gets summed with transmit voice or signaling, • DTMF data for telephone communication in trunked and conventional systems, and • Audible signaling including MDC and high-speed trunking. Note: All three types are supported by the hardware while the radio software determines which signaling type is available. 8.1 Sub-Audio Data (PL/DPL) Sub-audible data implies signaling whose bandwidth is below 300Hz. PL and DPL waveforms are used for conventional operation and connect tones for trunked voice channel operation. The trunking connect tone is simply a PL tone at a higher deviation level than PL in a conventional system. Although it is referred to as “sub-audible data”, the actual frequency spectrum of these waveforms may be as high as 250 Hz, which is audible to the human ear. However, the radio receiver filters out any audio below 300Hz, so these tones are never heard in the actual system. Only one type of sub-audible data can be generated by U504 (ASFIC CMP) at any one time. The process is as follows, using the SPI BUS, the µP programs the ASFIC CMP to set up the proper lowspeed data deviation and select the PL or DPL filters. The µP then generates a square wave which strobes the ASFIC PL / DPL encode input LSIO U504-pin 18 at twelve times the desired data rate. For example, for a PL frequency of 103Hz, the frequency of the square wave would be 1236Hz. This drives a tone generator inside U504 which generates a staircase approximation to a PL sine wave or DPL data pattern. This internal waveform is then low-pass filtered and summed with voice or data. The resulting summed waveform then appears on U504-pin 40 (MOD IN), where it is sent to the RF board as previously described for transmit audio. A trunking connect tone would be generated in the same manner as a PL tone. 2-18 8.2 THEORY OF OPERATION High Speed Data High speed data refers to the 3600 baud data waveforms, known as Inbound Signaling Words (ISWs) used in a trunking system for high speed communication between the central controller and the radio. To generate an ISW, the µP first programs the ASFIC CMP (U504) to the proper filter and gain settings. It then begins strobing U504-pin 19 (HSIO) with a pulse when the data is supposed to change states. U504’s 5-3-2 State Encoder (which is in a 2-state mode) is then fed to the postlimiter summer block and then the splatter filter. From that point it is routed through the modulation attenuator and then out of the ASFIC CMP to the RF board. MDC is generated in much the same way as trunking ISW. However, in some cases these signals may also pass through a data preemphasis block in the ASFIC CMP. Also these signaling schemes are based on sending a combination of 1200 Hz and 1800 Hz tones only. Microphone audio is muted during high speed data signaling. 8.3 Dual Tone Multiple Frequency (DTMF) Data DTMF data is a dual tone waveform used during phone interconnect operation. It is the same type of tones which are heard when using a “Touch Tone” telephone. There are seven frequencies, with four in the low group (697, 770, 852, 941Hz) and three in the high group (1209, 1336, 1477Hz). The high-group tone is generated by the µP (U403-46) strobing U50419 at six times the tone frequency for tones less than 1440Hz or twice the frequency for tones greater than 1440Hz. The low group tone is generated by the ASFIC CMP, controlled by the µP via SPI bus. Inside U504 the low-group and high-group tones are summed (with the amplitude of the high group tone being approximately 2 dB greater than that of the low group tone) and then preemphasized before being routed to the summer and splatter filter. The DTMF waveform then follows the same path as was described for high-speed data. Receive Audio Circuits 9.0 2-19 Receive Audio Circuits ACCESSORY CONNECTOR 11 1 AUDIO PA U502 9 4 SPKR + 16 SPKR - 1 EXTERNAL SPEAKER 6 INT SPKR+ INT SPKRCONTROL HEAD CONNECTOR 19 MUTE U509 FLT RX AUDIO P1 INTERNAL SPEAKER 20 J2 18 HANDSET AUDIO U505 37 39 10 GCB4 U IO 43 AUX RX 14 41 URX OUT AUDIO GCB1 VOLUME ATTEN. ASFIC_CMP U504 FILTER AND DEEMPHASIS DISC FROM AUDIO RF SECTION (IF IC) 2 DISC PL FILTER LIMITER LIMITER, RECTIFIER FILTER, COMPARATOR LS IO 18 SQUELCH CIRCUIT SQ DET CH ACT 16 17 84 83 MICRO CONTROLLER 80 U403 85 Figure 2-9 Receive Audio Paths 9.1 Squelch Detect The radio’s RF circuits are constantly producing an output at the discriminator (IF IC). This signal (DISC AUDIO) is routed to the ASFIC CMP’s squelch detect circuitry input DISC (U504-pin 2). All of the squelch detect circuitry is contained within the ASFIC CMP. Therefore from a user’s point of view, DISC AUDIO enters the ASFIC CMP, and the ASFIC CMP produces two CMOS logic outputs based on the result. They are CH ACT (U504-16) and SQ DET (U504-17). The squelch signal entering the ASFIC CMP is amplified, filtered, attenuated, and rectified. It is then sent to a comparator to produce an active high signal on CH ACT. A squelch tail circuit is used to produce SQ DET (U504-17) from CH ACT. The state of CH ACT and SQ DET is high (logic “1”) when carrier is detected, otherwise low (logic “0”). CH ACT is routed to the µP pin 84 while SQ DET is routed to the µP pin 83. SQ DET is used to determine all audio mute / unmute decisions except for Conventional Scan. In this case CH ACT is a pre-indicator as it occurs slightly faster than SQ DET. 2-20 9.2 THEORY OF OPERATION Audio Processing and Digital Volume Control The receiver audio signal (DISC AUDIO) enters the controller section from the IF IC where it is.DC coupled to ASFIC CMP via the DISC input U504-pin 2. The signal is then applied to both the audio and the PL/DPL paths The audio path has a programmable amplifier, whose setting is based on the channel bandwidth being received, an LPF filter to remove any frequency components above 3000Hz, and a HPF to strip off any sub-audible data below 300Hz. Next, the recovered audio passes through a deemphasis filter (if it is enabled to compensate for Pre-emphasis which is used to reduce the effects of FM noise). The IC then passes the audio through the 8-bit programmable attenuator whose level is set depending on the value of the volume control. Finally the filtered audio signal passes through an output buffer within the ASFIC CMP. The audio signal exits the ASFIC CMP at AUDIO output (U504 pin 41). The µP programs the attenuator, using the SPI BUS, based on the volume setting. The minimum / maximum settings of the attenuator are set by codeplug parameters. Since sub-audible signaling is summed with voice information on transmit, it must be separated from the voice information before processing. Any sub-audible signaling enters the ASFIC CMP from the IF IC at DISC U504-2. Once inside, it goes through the PL/DPL path. The signal first passes through one of the two low-pass filters, either the PL low-pass filter or the DPL/LST low-pass filter. Either signal is then filtered and goes through a limiter and exits the ASFIC CMP at LSIO (U504-pin 18). At this point, the signal will appear as a square wave version of the sub-audible signal which the radio received. The µP U403 pin 80 will decode the signal directly to determine if it is the tone / code which is currently active on that mode. 9.3 Audio Amplification Speaker (+) Speaker (-) The output of the ASFIC CMP’s digital volume pot, U504-pin 41 is routed through DC blocking capacitor C5049 to the audio PA (U502 pin 1 and 9). The audio power amplifier has one inverted and one non-inverted output that produces the differential audio output SPK+/SPK- (U502 pins 4 and 6) The audio PA is enabled via the ASFIC CMP (U504-GCB1). When the base of Q501 is low, the transistor is off and U502-pin 8 is high, using pull up resistor R5041, and the audio PA is ON. The voltage at U502-pin 8 must be above 8.5Vdc to properly enable the device. If the voltage is between 3.3 and 6.4V, the device will be active but has its input (U502-pins 1/9) off. This is a mute condition which is used to prevent an audio pop when the PA is enabled. The SPK+ and SPK- outputs of the audio PA have a DC bias which varies proportionately with B+ (U502- pin 7). B+ of 11V yields a DC offset of 5V, and B+ of 17V yields a DC offset of 8.5V. If either of these lines is shorted to ground, it is possible that the audio PA will be damaged. SPK+ and SPKare routed to the accessory connector (P1-pin 1 and 16) and to the control head (connector J2-pins 19 and 20). Receive Signalling Circuits 9.4 2-21 Handset Audio Certain handheld accessories have a speaker within them which require a different voltage level than that provided by U502. For these devices HANDSET AUDIO is available at control head connector J2 pin18. The received audio from the output of the ASFIC CMP’s digital volume attenuator is routed to U505 pin 2 where it is amplified. This signal is routed from the output of the op-amp U505 to J2-pin 18. From the control head, the signal is sent directly to the microphone jack. 9.5 Filtered Audio and Flat Audio The ASFIC CMP output audio at U504-pin 39 is filtered and de-emphasized, but has not gone through the digital volume attenuator. From ASFIC CMP U504-pin 39 the signal is routed via R5034 through gate U509-pin 12 and AC coupled to U505-pin 6. The gate controlled by ASFIC CMP port GCB4 selects between the filtered audio signal from the ASFIC CMP pin 39 (URXOUT) or the unfiltered (flat) audio signal from the ASFIC CMP pin 10 (UIO). Resistors R5034 and R5021 determine the gain of op-amp UU505-pin 6 for the filtered audio while R5032 and R5021 determine the gain for the flat Audio. The output of U505-pin 7 is then routed to P1 pin 11 via DC blocking capacitor C5003. Note that any volume adjustment of the signal on this path must be done by the accessory. 10.0 Receive Signalling Circuits DATA FILTER AND DEEMPHASIS DET AUDIO DISCRIMINATOR AUDIO FROM RF SECTION (IF IC) 2 LIMITER HSIO 19 82 44 DISC ASFIC_CMP U504 FILTER LIMITER MICRO CONTROLLER U403 LSIO 18 80 85 PLEAP 8 PLCAP2 25 Figure 2-10 Receive Signalling Paths 10.1 Sub-Audio Data (PL/DPL) and High Speed Data Decoder The ASFIC CMP (U504) is used to filter and limit all received data. The data enters the ASFIC CMP at input DISC (U504 pin 2). Inside U504 the data is filtered according to data type (HS or LS), then it is limited to a 0-3.3V digital level. The MDC and trunking high speed data appear at U504-pin 19, where it connects to the µP U403 pin 80. 2-22 THEORY OF OPERATION The low speed limited data output (PL, DPL, and trunking LS) appears at U504-pin18, where it connects to the µP U403-pin 80. The low speed data is read by the µP at twice the frequency of the sampling waveform; a latch configuration in the ASFIC CMP stores one bit every clock cycle. The external capacitors C5028, and C5026 set the low frequency pole for a zero crossings detector in the limiters for PL and HS data. The hysteresis of these limiters is programmed based on the type of received data. 10.2 Alert Tone Circuits When the software determines that it needs to give the operator an audible feedback (for a good key press, or for a bad key press), or radio status (trunked system busy, phone call, circuit failures), it sends an alert tone to the speaker. It does so by sending SPI BUS data to U504 which sets up the audio path to the speaker for alert tones. The alert tone itself can be generated in one of two ways: internally by the ASFIC CMP, or externally using the µP and the ASFIC CMP. The allowable internal alert tones are 304, 608, 911, and 1823Hz. In this case a code contained within the SPI BUS load to the ASFIC CMP sets up the path and determines the tone frequency, and at what volume level to generate the tone. (It does not have to be related to the voice volume setting.) For external alert tones, the µP can generate any tone within the 100-3000Hz audio band. This is accomplished by the µP generating a square wave which enters the ASFIC CMP at U504 pin 19. Inside the ASFIC CMP this signal is routed to the alert tone generator. The output of the generator is summed into the audio chain just after the RX audio de-emphasis block. Inside U504, the tone is amplified and filtered, then passed through the 8-bit digital volume attenuator, which is typically loaded with a special value for alert tone audio. The tone exits at U504pin 41 and is routed to the audio PA like receive audio. Chapter 3 TROUBLESHOOTING CHARTS This section contains detailed troubleshooting flowcharts. These charts should be used as a guide in determining the problem areas. They are not a substitute for knowledge of circuit operation and astute troubleshooting techniques. It is advisable to refer to the related detailed circuit descriptions in the theory of operation sections prior to troubleshooting a radio. Most troubleshooting charts end up by pointing to an IC to replace. It is not always noted, but it is good practice to verify supplies and grounds to the affected IC and to trace continuity to the malfunctioning signal and related circuitry before replacing any IC. For instance, if a clock signal is not available at a destination, continuity from the source IC should be checked before replacing the source IC. 3-2 1.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2) START Problem in 12 KHz and 25 KHz channel spacing Go to DC Section 9V on Yes R310 (LNA) OK ? No Check RX_EN Go to DC Section No 3V to U301 Okay ? Yes Check Q306, Q300 and U403 Check Q304, D305 and U403 Go to SYN Section Go to DC Section No No RX_EN ON ? Yes LOC_DIST ON? Yes Check LOC_DIST Check TPI No LO POWER OK ? Yes Check 5V on R337 ) No 5V Yes (IF AMP) OK ? Check 3V on R339 Go to A Check D301-304 Replace IF Filters( FL304, FL301) If problem in 25 KHz spacing Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2) 1.1 3-3 Troubleshooting Flow Chart for Receiver (Sheet 2 of 2) From A 3V (IFIC -Vcc) OK ? Go to DC Section No Check the component No Antenna to Mixer circuitry problem No Check visually all receiver components installation ? Yes Installation OK ? Yes Inject - 40dBm (CW) to RF connector Check Power on C335 RF Yes Power > -28 dBM? Check Power on C337 Replace Q305, Q300, U302 Check passive components Replace Q303, Q301 Check passive components No Replace Y301 No Go to DC Section 3V to U301 OK? Yes Y301 OK? No Yes RF Yes Power > -28 dBM? Replace Q302, Y300 Check D301 - 304 Replace U300 Check Y301 44.395 MHz 3-4 2.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 40W Transmitter (Sheet 1 of 3) START No or too low power when keyed Check components between Q100 and RF output, Antenna Switch D104, D103, VR102 and Q106 >4A Current increase when keyed? >500mA & <4A <500mA Check PA Stages Yes Control Voltage at TP150 >4Vdc? No Check 9.3V Regulator U501 No Voltage U103 pin 5 = 4.7V? Yes Check power settings, tuning & components between U103 Pin 3 and ASFIC Pin 6 before replacing ASFIC No U103 Pin 3 <1.6Vdc Yes Check U103 Yes Short U100 Pin 3 to ground U100 Pin 3 >1.8Vdc No Check forward Power Sense Circuit Check PA Stages Yes Voltage at TP150 rises? No Check Forward Power Sense Circuit Troubleshooting Flow Chart for 40W Transmitter (Sheet 1 of 3) 2.1 3-5 Troubleshooting Flow Chart for 40W Transmitter (Sheet 2 of 3) Check PA Stages No or too low power when keyed DC Voltage at Q101 & Q102 base=0? Check Q102, Q101, R122, R165 No Check U510 Yes No DC Voltage at U103 Pin 10=8.9V <2V Yes DC Voltage at U103 Pin 8 >5V Check resistive network at Pin 9 and 10 of U103 before replacing U101 2 to 5V Check U103 and Resistive Network at Pin 10 of U103 before replacing U101 Measure DC Voltage at Pin 2 & 3 of U5401 Pin 2 Voltage 0.62 x Voltage at Pin 1 No Replace U5410 Yes Check bias tuning before replacing U504 Pin 3 Voltage 0.51 x Voltage at Pin 1 No ASFIC U504 Pin 5 2-3V Yes Check components between ASFIC and Q105 before replacing Q105 0V No Replace U5410 Yes DC Voltage at Supply Voltage PA_CURRENT line? 2-3V Check Final PA Stages Replace Q105 3-6 2.2 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 40W Transmitter (Sheet 3 of 3) Check Final PA Stage Check components between ASFIC & Q100 before replacing Q100 Yes 0V PA_Bias Voltage at R134 Supply Voltage Replace Q100 1-4V RF Voltage after C1044 >100mV? RF Voltage after C1044 >100mV? No Check FGU (U5301) No Check Bias Tuning before replacing ASFIC U504 Yes Voltage across R122 >2V? No Check components between C1044 & C1117 No Check components between C117 & Q105 No Check components between Q105 & Q100 Yes RF Voltage Q105 gate >1V? Yes RF Voltage Q100 gate >7V? Yes Check components between Q100 & antenna connector Troubleshooting Flow Chart for Synthesizer 3.0 3-7 Troubleshooting Flow Chart for Synthesizer Start NO Correct Problem Check D200, D201, C2026, C2025, & C2027 3.3V at U200 pins 5, 20, 34 & 36 Visual check of the Board OK? NO Check 3V Regulator U503 YES YES YES 5V at pin 6 of D200 NO Is U200 Pin 47 at = 14.6VDC ? NO +5V at U200 Pin’s 13 & 30 ? NO YES Check R228 Check R201 Is U201 Pin 19 <40 mVDC in RX & >4.5 VDC in TX? (at VCO section) ? NO Are Waveforms at Pins 14 & 15 triangular ? NO YES NO NO Is there a short between Pin 47 and Pins 14 & 15 of U200 ? Check programming lines between U403 and U200 Pins 7,8 & 9 NO YES Remove Shorts Is RF level at U200 Pin 32 -12 < x <-25 dBm ? YES Replace U200 NO Replace U200 NO YES NO Replace U200 YES YES Check Y201 and associated Parts Are signals at Pin’s 14 &15 of U200 ? YES Is U200 Pin 2 >4.5 VDC in Tx & <40 mVDC in Rx ? Is 16.8MHz signal at U200 Pin 23? NO Check 5V Regulator U503 NO YES YES Is 16.8MHz Signal at U200 Pin 19 ? If C2052, R208,C2067, C2068, L210 are OK, then see VCO troubleshooting chart Check uP U403 Troubleshooting Chart Do Pins 7,8 & 9 of U200 toggle when channel is changed? YES Is information from uP U403 correct ? YES Replace U200 3-8 TROUBLESHOOTING CHARTS 4.0 Troubleshooting Flow Chart for VCO RX VCO Low or no RF Signal at input to PA Low or no RF Signal at TP1 Visual check of board OK? NO Correct Problem NO Visual check of board OK? YES YES Make sure Synthesizer is working correctly and runner between U200 Pin 28 and U201 Pin 14 & 18 is OK NO 4.5V DC at U201 Pin 14 & 18 OK ? 4.5V DC at U201 Pin 14 & 18 OK ? NO YES YES 370mV DC at U201 Pin 19 OK? TX VCO Check runner between U200 Pin 2 and U201 Pin 19 NO NO 4.5V DC at U201 Pin 19 OK? YES Is RF available at base of Q200 YES NO Are U201 Pins 15 at 1.0V 10 at 3.9V 16 at 1.8V Replace U201 YES Are Q200 Base at 2.9V Collector at 6.6V Emitter at 2.2V If all parts associated with the pins are OK, replace U201 NO YES NO If all parts associated with the pins are OK, replace Q200 NO Is RF available at C2060 If parts between R109 & U201 Pin10 are OK, replace U201 YES YES Check parts to pre-driver If all parts from collector of Q200 to TP1 are OK, replace Q200 Power OK but no modulation Audio =180mVRMS at “-” Side of NO Replace R212 D205 YES 4.5VDC at D205 NO YES If R211 and R12 are OK, then replace D205 Replace R211 Troubleshooting Flow Chart for DC Supply (1 of 2) 5.0 3-9 Troubleshooting Flow Chart for DC Supply (1 of 2) Since the failure of a critical voltage supply might cause the radio to automatically power down, supply voltages should first be probed with a multimeter. If all the board voltages are absent, then the voltage test point should be retested using a rising-edge-triggered oscilloscope. If the voltage is still absent, then another voltage should be tested using the oscilloscope. If that voltage is present, then the original voltage supply in question is defective and requires investigation of associated circuitry. 5V Check VDC on C5006 Go to 3V Replace U503 Yes Yes V=5V ? 9v 1 GHz Adjacent Channel Power -60dB @12.5, -70dB @ 20/25kHz Audio Response: ( 300 to 3000Hz) +1, -3dB Audio Distortion: @ 1000 Hz, 60% Rated Maximum Deviation: 3% Typical Receiver Specification Sensitivity (12dBSINAD): (ETS) Intermodulation : (ETS) Adjacent Channel Selectivity: (ETS) Spurious Rejection: (ETS) Rated Audio: (ETS) (Extended audio with 4 Ohm speaker) Audio Distortion @ Rated Audio: VHF2 0.35µV (12.5kHz) 0.30µV (25kHz) Typical >65dB 75 dB @ 25 kHz 65 dB @ 12.5 kHz 75 dB 4W Internal , 13W External 3% Typical Hum and Noise: -40 dB @ 12.5 kHz -45 dB @ 20/25 kHz Audio Response: ( 300 to 3000Hz) +1, -3dB Conducted Spurious Emission per FCC Part 15: -57 dBm <1 GHz -47 dBm >1 GHz *Availability subject to the laws and regulations of individual countries. 1-4 MODEL CHART AND TECHNICAL SPECIFICATIONS Chapter 2 THEORY OF OPERATION 1.0 Introduction This Chapter provides a detailed theory of operation for the VHF circuits in the radio. Details of the theory of operation and trouble shooting for the the associated Controller circuits are included in this Section of the manual. 2.0 VHF (146-174MHz) Receiver 2.1 Receiver Front-End The received signal is applied to the radio’s antenna input connector and routed through the harmonic filter and antenna switch. The insertion loss of the harmonic filter/antenna switch is less than 1 dB. The signal is routed to the first filter (4-pole), which has an insertion loss of 2 dB typically. The output of the filter is matched to the base of the LNA (Q303) that provides a 16 dB gain and a noise figure of better than 2 dB. Current source Q301 is used to maintain the collector current of Q303. Diode CR301 protects Q303 by clamping excessive input signals. Q303 output is applied to the second filter (3-pole) which has an insertion loss of 1.5 dB. In Distance mode, Q304 turns on and causes D305 to conduct, thus bypassing C322 and R337. In Local mode, the signal is routed through C322 and R337, thus inserting 7 dB attenuation. Since the attenuator is located after the RF amplifier, the receiver sensitivity is reduced only by 6 dB, while the overall third order input intercept is raised. The first mixer is a passive, double-balanced type, consisting of T300, T301 and U302. This mixer provides all of the necessary rejection of the half-IF spurious response. High-side injection at +15 dBm is delivered to the first mixer. The mixer output is then connected to a duplex network which matches its output to the XTAL filter input (FL300) at the IF frequency of 44.85 MHz. The duplex network terminates into a 50 ohm resistor (R340) at all other frequencies. Antenna Front Filter 12.5kHzFilter 12.5kHzFilter LNA Second Filter Mixer 4- Pole Xtal Filter IF Amp First LO 25kHzFilter 25kHzFilter IFIC 2nd LO Xtal Osc Phase Shift Element Controller Figure 2-1 VHF Receiver Block Diagram 2-2 THEORY OF OPERATION 2.2 Receiver Back End The IF signal from the crystal filter enters the IF amplifier which provides 20 dB of gain and feeds the IF IC at pin 1. The first IF signal at 44.85 MHz mixes with the second local oscillator (LO) at 44.395 MHz to produce the second IF at 455 kHz. The second LO uses the external crystal Y301. The second IF signal is amplified and filtered by two external ceramic filters (FL303/FL302 for 12.5KHz channel spacing and FL304/FL301 for 25KHz channel spacing). The IF IC demodulates the signal by means of a quadrature detector and feeds the detected audio (via pin 7) to the audio processing circuits. At IF IC pin 5, an RSSI signal is available with a dynamic range of 70 dB. 3.0 VHF Transmitter Power Amplifier (146-174 MHz) The radio’s 45W PA is a three-stage amplifier used to amplify the output from the TX_INJ to the antenna port. All three stages utilize LDMOS technology. The gain of the first stage (U101) is adjustable and is controlled by pin 7 of U103-2 via U103-3 and U102-1. It is followed by an LDMOS driver Q105 and final stage Q100. Pin Diode Antenna Switch From VCO (TX_INJ) Controlled Stage PA PA-Final Stage Driver Harmonic Filter RF Jack Coupler Bias Bias Antenna Forward A S FI C _C M P SPI BUS PA PWR SET L oo p C ont r ol le r U 103 - 2 Temperature Sense Figure 2-2 VHF Transmitter Block Diagram Devices U101, Q105 and Q100 are surface mounted.Two screws with Belleville washers provide direct pressure ensuring good thermal contact between both the driver and final stage, and the chassis. 3.1 First Power Controller Stage The first stage (U101) is a 20dB gain integrated circuit containing two LDMOS FET amplifier stages. It amplifies the RF signal from the VCO (TX_INJ). The output power of stage U101 is controlled by a DC voltage applied to pin 1 from the op-amp U103-3, pin 8. The control voltage simultaneously varies the bias of two FET stages within U101. This biasing point determines the overall gain of U101 and therefore its output drive level to Q105, which in turn controls the output power of the PA. VHF Transmitter Power Amplifier (146-174 MHz) 2-3 Op-amp U103-3 monitors the drain current of U101 via resistor R122 and adjusts the bias voltage of U101. In receive mode, the DC voltage from RX_EN line turns on Q101, which in turn switches off the biasing voltage to U101. 3.2 Power Controlled Driver Stage The next stage is an LDMOS device (Q105) which provides a gain of 12dB. This device requires a positive gate bias and a quiescent current flow for proper operation. The bias is set during transmit mode by the V_cntrl_driver which is set to provide 100-150mA of quiescent current by the factory, and fed to the gate of Q105 via the resistive network. The V_cntrl_driver is directly controlled by the ASFIC CMP. In receive mode, the ASFIC CMP (U504) sets V_cntrl_driver to 0V (DACR pin 5). 3.3 Final Stage The final stage is an LDMOS device (Q100) providing a gain of 12dB. This device also requires a positive gate bias and a quiescent current flow for proper operation. The voltage of the line PA_BIAS is set in transmit mode by the ASFIC and fed to the gate of Q100 via the resistive network R134, R131. This bias voltage is tuned in the factory. If the transistor is replaced, the bias voltage must be tuned using the Tuner. Care must be taken not to damage the device by exceeding the maximum allowed bias voltage. The device’s drain current is drawn directly from the radio’s DC supply voltage input, B+, via L117 and L115. A matching network consisting of C1004-5, C1007-9, C1096, C1021, C1013, C1019, L116: and two striplines, transforms the impedance to 50 ohms and feeds the directional coupler. 3.4 Bi-Directional Coupler The bi-directional Coupler is a microstrip printed circuit, which couples a small amount of the forward and reverse power of the RF power from Q100.The coupled signal is rectified to an output power which is proportional to the DC voltage rectified by diode D105; and the resulting DC voltage is routed to the power control section to ensure that the forward power out of the radio is held to a constant value. 3.5 Antenna Switch The antenna switch utilizes the existing dc feed (B+) to the last stage device (Q100). The basic operation is to have both PIN diodes (D103, D104) turned on during key-up by forward biasing them. This is achieved by pulling down the voltage at the cathode end of D104 to around 12.4V (0.7V drop across each diode). The current through the diodes needs to be set around 100 mA to fully open the transmit path through resistor R108. Q106 is a current source controlled by Q103 which is turned on in Tx mode by TX_EN. VR102 ensures that the voltage at resistor R107 never exceeds 5.6V. 2-4 3.6 THEORY OF OPERATION Harmonic Filter Inductors L111, L112, L124 and L113 along with capacitors C11321, C1022, C1020, C1137, C1018 and C1017 form a low-pass filter to attenuate harmonic energy coming from the transmitter. Resistor R150 drains any electrostatic charges that might otherwise build up on the antenna. The harmonic filter also prevents high level RF signals above the receiver passband from reaching the receiver circuits to improve spurious response rejection. 3.7 Power Control The output power is regulated by using a forward power detection control loop. A directional coupler samples a portion of the forward and reflected RF power. The forward sampled RF is rectified by diode D105, and the resulting DC voltage is routed to the operational amplifier U100. The error output current is then routed to an integrator, and converted into the control voltage. This voltage controls the bias of the pre-driver (U101) stage. The output power level is set by way of a DAC, PWR_SET, in the audio processing IC (U504), which acts at the forward power control loop reference. The sampled reflected power is rectified by diode D107. The resulting DC voltage is amplified by an operational amplifier U100 and routed to the summing junction. This detector protects the final stage Q100 from reflected power by increasing the error current. The temperature sensor protects the final stage Q100 from overheating by increasing the error current. A thermistor RT100 measures the final stage Q100 temperature. The voltage divider output is routed to an operational amplifier U103 and then goes to the summing junction. The Zener Diode VR101 keeps the loop control voltage below 5.6V and eliminates the DC current from the 9.3 regulator U501. A local loop for the Pre Driver (U101) is used in order to stabilize the current for each stage. In Rx mode, the two transistors Q101 and Q102 go to saturation and shut down the transmitter by applying ground to the Pre Driver U101. 4.0 VHF (146-174MHz) Frequency Synthesis The synthesizer consists of a reference oscillator (Y201), low voltage Fractional-N (LVFRAC-N) synthesizer (U200), and a voltage controlled oscillator (VCO) (U201). 4.1 Reference Oscillator The reference oscillator is a crystal (Y201) controlled Colpitts oscillator and has a frequency of 16.8MHz. The oscillator transistor and start-up circuit are located in the LVFRAC-N (U200) while the oscillator feedback capacitors, crystal, and tuning varactors are external. An analog-to-digital (A/D) converter internal to the LVFRAC-N (U200) and controlled by the microprocessor via SPI sets the voltage at the warp output of U200 pin 25. This sets the frequency of the oscillator. Consequently, the output of the crystal Y201 is applied to U200 pin 23. The method of temperature compensation is to apply an inverse Bechmann voltage curve, which matches the crystal’s Bechmann curve to a varactor that constantly shifts the oscillator back on frequency. The crystal vendor characterizes the crystal over a specified temperature range and codes this information into a bar code that is printed on the crystal package. In production, this crystal code is read via a 2-dimensional bar code reader and the parameters are saved. VHF (146-174MHz) Frequency Synthesis 2-5 This oscillator is temperature compensated to an accuracy of +/-2.5 PPM from -30 to 60 degrees C. The temperature compensation scheme is implemented by an algorithm that uses five crystal parameters (four characterize the inverse Bechmann voltage curve and one for frequency accuracy of the reference oscillator at 25 degrees C). This algorithm is implemented by the LVFRAC-N (U200) at the power up of the radio. 4.2 Fractional-N Synthesizer The LVFRAC-N U200 consists of a pre-scaler, programmable loop divider, control divider logic, phase detector, charge pump, A/D converter for low frequency digital modulation, balanced attenuator used to balance the high and low frequency analog modulation, 13V positive voltage multiplier, serial interface for control, and a super filter for the regulated 5 volts. DATA (U403 PIN 100) CLOCK (U403 PIN 1) CSX (U403 PIN 2) MOD IN (U501 PIN 40) +5V (U503 PIN 1) +5V (U503 PIN 1) 7 8 9 10 13, 30 5, 20, 34, 36 REFERENCE OSCILLATOR 23 24 VOLTAGE MULTIPLIER FREFOUT CLK GND CEX MODIN VCC, DC5V IOUT IADAPT VDD, DC5V MODOUT XTAL1 U200 XTAL2 FRACTIONAL-N SYNTHESIZER 25 WARP 32 PREIN 47 LOCK DATA LOW VOLTAGE VCP VMULT2 14 15 48 43 45 LOOP FILTER STEERING LINE 41 AUX3 2 AUX1 BIAS2 FREF (U504 PIN 34) 6, 22, 33, 44 3 1 BIAS1 LOCK (U403 PIN 56) 19 AUX4 AUX2 SFOUT VMULT1 4 VCO Bias LO RF INJECTION TRB VOLTAGE 28 FILTERED 5V CONTROLLED OSCILLATOR 40 TX RF INJECTION (1ST STAGE OF PA) 39 BWSELECT To IF Section PRESCALER IN Figure 2-3 VHF Synthesizer Block Diagram A voltage of 5V applied to the super filter input (U200, pin 30) supplies an output voltage of 4.5Vdc (VSF) at U200, pin 28. This supplies 4.5 V to the VCO Buffer IC U201. To generate a high voltage to supply the phase detector (charge pump) output stage at pin VCP (U200, pin 47) while using a low voltage 3.3Vdc supply, a 13V positive voltage multiplier is used (D200, D201, and capacitors C2024, 2025, 2026, 2055, 2027, 2001). Output lock (U200, pin 4) provides information about the lock status of the synthesizer loop. A high level at this output indicates a stable loop. A 16.8 MHz reference frequency is provided at U200, pin 19. 2-6 THEORY OF OPERATION 4.3 Voltage Controlled Oscillator (VCO) The Voltage Controlled Oscillator (VCO) consists of the VCO/Buffer IC (VCOBIC, U201), the TX and RX tank circuits, the external RX amplifier, and the modulation circuitry. AUX3 (U200 Pin 2) Prescaler Out TRB IN Pin 20 Rx-SW Pin7 Tx-SW Pin13 (U200 Pin 28) Pin 19 U200 Pin 32 Pin 12 TX/RX/BS Switching Network Vcc-Superfilter Pin3 LO RF INJECTION Presc U201 VCOBIC Q200 Buffer Low Pass Filter Collector/RF in Steer Line Voltage (VCTRL) Pin4 RX Tank RX VCO Circuit TX VCO Circuit Rx Active Bias Pin5 Pin6 TX Tank RX RX Pin8 Pin14 TX Tx Active Bias Pin16 Pin15 TX Pin10 Vcc-Logic TX RF Injection Attenuator Vsens Circuit Pin18 (U200 Pin28) VCC Buffers Pin2 Pin1 Rx-I adjust Tx-I adjust Pins 9,11,17 (U200 Pin 28) Figure 2-4 VHF VCO Block Diagram The VCOBIC together with the LVFRAC-N (U200) generate the required frequencies in both transmit and receive modes. The TRB line (U201, pin 19) determines which VCO and buffer is enabled (high being TX output at pin 10, low being RX output at pin 8). A sample of the signal from the enabled output is routed from U201, pin 12 (PRESC_OUT), via a low pass filter to U200, pin 32 (PREIN). A steering line voltage between 3.0V and 10.0V at varactor D204 tunes the TX VCO through the frequency range of 146-174MHz, and at D203 tunes the RX VCO through the frequency range of 190-219MHz. The external RX amplifier is used to increase the output from U201, pin 9 from 3-4 dBm to the required 15dBm for proper mixer operation. In TX mode, the modulation signal from the LVFRAC-N (U200, pin 41) is applied to the VCO by way of the modulation circuit D205, R212, R211, C2073. VHF (146-174MHz) Frequency Synthesis 4.4 2-7 Synthesizer Operation The synthesizer consists of a low voltage FRAC-N IC (LVFRAC-N), reference oscillator, charge pump circuits, loop filter circuit, and DC supply. The output signal (PRESC_OUT) of the VCOBIC (U201, pin 12) is fed to the PREIN, pin 32 of U200 via a low pass filter which attenuates harmonics and provides a correct input level to the LVFRAC-N in order to close the synthesizer loop. The pre-scaler in the synthesizer (U200) is a dual modulus pre-scaler with selectable divider ratios. The divider ratio of the pre-scaler is controlled by the loop divider, which in turn receives its inputs via the SPI. The output of the pre-scaler is applied to the loop divider. The output of the loop divider is connected to the phase detector, which compares the loop divider’s output signal with the reference signal. The reference signal is generated by dividing down the signal of the reference oscillator (Y201). The output signal of the phase detector is a pulsed dc signal that is routed to the charge pump. The charge pump outputs a current from U200, pin 43 (IOUT). The loop filter (consisting of R224, R217, R234, C2074, C2075, C2077, C2078, C2079, C2080, C2028, and L205) transforms this current into a voltage that is applied the varactor diodes D203 and D204 for RX and TX respectively. The output frequency is determined by this control voltage. The current can be set to a value fixed in the LVFRAC-N or to a value determined by the currents flowing into BIAS 1 (U200, pin 40) or BIAS 2 (U200, pin 39). The currents are set by the value of R200 or R206 respectively. The selection of the three different bias sources is done by software programming. To modulate the synthesizer loop, a two-spot modulation method is utilized via the MODIN (U200, pin 10) input of the LVFRAC-N. The audio signal is applied to both the A/D converter (low frequency path) and the balance attenuator (high frequency path). The A/D converter converts the low frequency analog modulating signal into a digital code which is applied to the loop divider, thereby causing the carrier to deviate. The balance attenuator is used to adjust the VCO’s deviation sensitivity to high frequency modulating signals. The output of the balance attenuator is presented at the MODOUT port of the LVFRAC-N (U200,pin 41) and connected to the VCO modulation varactor D205. 2-8 5.0 THEORY OF OPERATION Controller Theory of Operation This section provides a detailed theory of operation for the radio and its components. The main radio is a single-board design, consisting of the transmitter, receiver, and controller circuits. A control head is connected by an extension cable. The control head contains LED indicators, a microphone connector, buttons, and speaker. In addition to the power cable and antenna cable, an accessory cable can be attached to a connector on the rear of the radio. The accessory cable enables you to connect accessories to the radio, such as an external speaker, emergency switch, foot-operated PTT, and ignition sensing, etc. External Microphone To Synthesizer Mod Out 16.8 MHz Reference Clock from Synthesizer Audio/Signaling Architecture Disc Audio ASFIC_CMP . Internal Microphone External Speaker Audio PA Internal Speaker µP Clock SPI To RF Section Digital Architecture SCI to Accessory & Control Head Connector RAM EEPROM 3.3V Regulator HC11FL0 FLASH Figure 2-5 Controller Block Diagram 5.1 Radio Power Distribution Voltage distribution is provided by five separate devices: ■ U514 P-cH FET - Batt + (Ext_SWB+) ■ U501 LM2941T - 9.3V ■ U503 LP2951CM - 5V ■ U508 MC 33269DTRK - 3.3V ■ U510 LP2986ILDX - 3.3V Digital Handset Controller Theory of Operation 2-9 The DC voltage applied to connector P2 supplies power directly to the following circuitry: ■ Electronic on/off control ■ RF power amplifier ■ 12 volts P-cH FET -U514 ■ 9.3 volt regulator ■ Audio PA Ignition Auto On/Off Switch Control B+ Control Head RF_PA Audio_PA Mic Connector Ferrite Bit Filt_B+ Antenna Switch Power Control 500mA FET P-CH On/Off Control SW_Filt_B+ 11-16.6V 0.9A Status LEDs 7_Seg 7_Seg DOT Bed to 7-Seg Back light Shift Reg Acces Conn Audio PA_Soutdown Power Loop Op_Amp 9.3V 65mA U501 9.3V Regulator Keypad Mic Bias 9V, 5mA 0.85A Reset 9.3V 45mA On/Off Control U503 5V RF Regulator 500mA Rx_Amp PA_Pre-driver PA Driver 3.2V 72mA 45mA LVFRAC_N IF_Amp 9.3V 75mA 9.3V 162mA U508 3.3V RF Reg 50mA 25mA ASFIC_CMP IFIC RX Cct U510 3.3V D Reg 90mA micro P RAM Flash EEPROM Figure 2-6 DC Power Distribution Block Diagram Regulator U501 is used to generate the 9.3 volts required by some audio circuits, the RF circuitry and power control circuitry. Input and output capacitors are used to reduce high frequency noise. Resistors R5001 / R5081 set the output voltage of the regulator. This regulator output is electronically enabled by a 0 volt signal on pin 2. Q502, Q505 and R5038 are used to disable the regulator when the radio is turned off. Voltage regulator U510 provides 3.3 volts for the digital circuitry. Operating voltage is from the regulated 9.3V supply. Input and output capacitors are used to reduce high frequency noise and provide proper operation during battery transients. U510 provides a reset output that goes to 0 volts if the regulator output goes below 3.1 volts. This is used to reset the controller to prevent improper operation. Voltage regulator U508 provides 3.3V for the RF circuits and ASFIC_CMP. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. 2-10 THEORY OF OPERATION Voltage regulator U503 provides 5V for the RF circuits. Input and output capacitors are used to reduce the high frequency noise and provide proper operation during battery transients. VSTBY is used only for CM360 5-tone radios. The voltage VSTBY, which is derived directly from the supply voltage by components R5103 and VR502, is used to buffer the internal RAM. Capacitor C5120 allows the battery voltage to be disconnected for a couple of seconds without losing RAM parameters. Dual diode D501 prevents radio circuitry from discharging this capacitor. When the supply voltage is applied to the radio, C5120 is charged via R5103 and D501. 5.2 Protection Devices Diode VR500 acts as protection against ESD, wrong polarity of the supply voltage, and load dump. VR692 - VR699 are for ESD protection. 5.3 Automatic On/Off The radio can be switched ON in any one of the following three ways: 5.3.1 ■ On/Off switch. (No Ignition Mode) ■ Ignition and On/Off switch (Ignition Mode) ■ Emergency No Ignition Mode When the radio is connected to the car battery for the first time, Q500 will be in saturation, Q503 will cut-off, Filt_B+ will pass through R5073, D500, and S5010-pin 6 (On/Off switch). When S5010 is ON, Filt_B+ will pass through S5010-pin5, D511, R5069, R5037 and base of Q505 and move Q505 into saturation. This pulls U501-pin2 through R5038, D502 to 0.2V and turns On U514 and U501 9.3V regulator which supplies voltage to all other regulators and consequently turns the radio on, When U504 (ASFIC_CMP) gets 3.3V, GCB2 goes to 3.3V and holds Q505 in saturation, for soft turn off. 5.3.2 Ignition Mode When ignition is connected for the first time, it will force high current through Q500 collector, This will move Q500 out of saturation and consequently Q503 will cut-off. S5010 pin 6 will get ignition voltage through R601 (for load dump), R610, (R610 & C678 are for ESD protection), VR501, R5074, and D500. When S5010 is ON, Filt_B+ passes through S5010-pin 5, D511, R5069, R5037 and base of Q505 and inserts Q505 into saturation. This pulls U501-pin 2 through R5038, D502 to 0.2V and turns on U514 and U501 9.3V regulator which supply voltage to all other regulators and turns the radio on, When U504 (ASFIC_CMP) get 3.3V supply, GCB2 goes to 3.3V and holds Q505 in saturation state to allow soft turn off, When ignition is off Q500, Q503 will stay at the same state so S5010 pin 6 will get 0V from Ignition, Q504 goes from Sat to Cut, ONOFF_SENSE goes to 3.3V and it indicates to the radio to soft turn itself by changing GCB2 to ‘0’ after de registration if necessary. Controller Theory of Operation 5.3.3 2-11 Emergency Mode The emergency switch (P1 pin 9), when engaged, grounds the base of Q506 via EMERGENCY _ACCES_CONN. This switches Q506 to off and consequently resistor R5020 pulls the collector of Q506 and the base of Q506 to levels above 2 volts. Transistor Q502 switches on and pulls U501 pin2 to ground level, thus turning ON the radio. When the emergency switch is released R5030 pulls the base of Q506 up to 0.6 volts. This causes the collector of transistor Q506 to go low (0.2V), thereby switching Q502 to off. While the radio is switched on, the µP monitors the voltage at the emergency input on the accessory connector via U403-pin 62. Three different conditions are distinguished: no emergency kit is connected, emergency kit connected (unpressed), and emergency press. If no emergency switch is connected or the connection to the emergency switch is broken, the resistive divider R5030 / R5049 will set the voltage to about 3.14 volts (indicates no emergency kit found via EMERGENCY_SENSE line). If an emergency switch is connected, a resistor to ground within the emergency switch will reduce the voltage on EMERGENCY _SENSE line, and indicate to the µP that the emergency switch is operational. An engaged emergency switch pulls line EMERGENCY _SENSE line to ground level. Diode VR503 limits the voltage to protect the µP input. While EMERGENCY _ACCES_CONN is low, the µP starts execution, reads that the emergency input is active through the voltage level of µP pin 64, and sets the DC POWER ON output of the ASFIC CMP pin 13 to a logic high. This high will keep Q505 in saturation for soft turn off. 5.4 Microprocessor Clock Synthesiser The clock source for the µP system is generated by the ASFIC CMP (U504). Upon power-up the synthesizer IC (FRAC-N) generates a 16.8 MHz waveform that is routed from the RF section to the ASFIC CMP pin 34. For the main board controller the ASFIC CMP uses 16.8 MHz as a reference input clock signal for its internal synthesizer. The ASFIC CMP, in addition to audio circuitry, has a programmable synthesizer which can generate a synthesized signal ranging from 1200Hz to 32.769MHz in 1200Hz steps. When power is first applied, the ASFIC CMP will generate its default 3.6864MHz CMOS square wave UP CLK (on U504 pin 28) and this is routed to the µP (U403 pin 90). After the µP starts operation, it reprograms the ASFIC CMP clock synthesizer to a higher UP CLK frequency (usually 7.3728 or 14.7456 MHz) and continues operation. The ASFIC CMP may be reprogrammed to change the clock synthesizer frequencies at various times depending on the software features that are executing. In addition, the clock frequency of the synthesizer is changed in small amounts if there is a possibility of harmonics of the clock source interfering with the desired radio receive frequency. The ASFIC CMP synthesizer loop uses C5025, C5024 and R5033 to set the switching time and jitter of the clock output. If the synthesizer cannot generate the required clock frequency it will switch back to its default 3.6864MHz output. Because the ASFIC CMP synthesizer and the µP system will not operate without the 16.8 MHz reference clock it (and the voltage regulators) should be checked first when debugging the system. 2-12 5.5 THEORY OF OPERATION Serial Peripheral Interface (SPI) The µP communicates to many of the IC’s through its SPI port. This port consists of SPI TRANSMIT DATA (MOSI) (U403-pin100), SPI RECEIVE DATA (MISO) (U403-pin 99), SPI CLK (U0403-pin1) and chip select lines going to the various IC’s, connected on the SPI PORT (BUS). This BUS is a synchronous bus, in that the timing clock signal CLK is sent while SPI data (SPI TRANSMIT DATA or SPI RECEIVE DATA) is sent. Therefore, whenever there is activity on either SPI TRANSMIT DATA or SPI RECEIVE DATA there should be a uniform signal on CLK. The SPI TRANSMIT DATA is used to send serial from a µP to a device, and SPI RECEIVE DATA is used to send data from a device to a µP. In the controller section, there are two IC’s on the SPI BUS, ASFIC CMP (U504 pin 22), and EEPROM (U400). In the RF sections there is one IC on the SPI BUS, the FRAC-N Synthesizer. The chip select line CSX from U403 pin 2 is shared by the ASFIC CMP and FRAC-N Synthesizer. Each of these IC’s check the SPI data and when the sent address information matches the IC’s address, the following data is processed. When the µP needs to program any of these Is it brings the chip select line CSX to a logic “0” and then sends the proper data and clock signals. The amount of data sent to the various IC’s are different; e.g., the ASFIC CMP can receive up to 19 bytes (152 bits). After the data has been sent the chip select line is returned to logic “1”. 5.6 SBEP Serial Interface The SBEP serial interface allows the radio to communicate with the Customer Programming Software (CPS), or the Universal Tuner via the Radio Interface Box (RIB) or the cable with internal RIB. This interface connects to the SCI pin via control head connector (J2-pin 17) and to the accessory connector P1-6 and comprises BUS+. The line is bi-directional, meaning that either the radio or the RIB can drive the line. The µP sends serial data and it reads serial data via pin 97. Whenever the µP detects activity on the BUS+ line, it starts communication. 5.7 General Purpose Input/Output The controller provides six general purpose lines (PROG I/O) available on the accessory connector P1 to interface to external options. Lines PROG IN 3 and 6 are inputs, PROG OUT 4 is an output and PROG IN OUT 8, 12 and 14 are bi-directional. The software and the hardware configuration of the radio model define the function of each port. ■ PROG IN 3 can be used as external PTT input, or others, set by the CPS. The µP reads this port via pin 72 and Q412. ■ PROG OUT 4 can be used as external alarm output, set by the CPS. Transistor Q401 is controlled by the µP (U403 pin 55) ■ PROG IN 6 can be used as normal input, set by the CPS. The µP reads this port via pin 73 and Q411. This pin is also used to communicate with the RIB if resistor R421 is placed. ■ DIG IN OUT 8,12,14 are bi-directional and use the same circuit configuration. Each port uses an output Q416, Q404, Q405 controlled by µP pins 52, 53, 54. The input ports are read through µP pins 74, 76, 77; using Q409, Q410, Q411 Controller Theory of Operation 5.8 2-13 Normal Microprocessor Operation For this radio, the µP is configured to operate in one of two modes, expanded and bootstrap. In expanded mode the µP uses external memory devices to operate, whereas in bootstrap operation the µP uses only its internal memory. In normal operation of the radio the µP is operating in expanded mode as described below. During normal operation, the µP (U403) is operating in expanded mode and has access to 3 external memory devices; U400 (EEPROM), U402 (SRAM), U404 (Flash). Also, within the µP there are 3 Kilobytes of internal RAM, as well as logic to select external memory devices. The external EEPROM (U400) space contains the information in the radio which is customer specific, referred to as the codeplug. This information consists of items such as: 1) what band the radio operates in, 2) what frequencies are assigned to what channel, and 3) tuning information. The external SRAM (U402) as well as the µP’s own internal RAM space are used for temporary calculations required by the software during execution. All of the data stored in both of these locations is lost when the radio powers off. The µP provides an address bus of 16 address lines (ADDR 0 - ADDR 15), and a data bus of 8 data lines (DATA 0 - DATA 7). There are also 3 control lines; CSPROG (U403-38) to chip select U404-pin 30 (FLASH), CSGP2 (U403-pin 41) to chip select U404-pin 20 (SRAM) and PG7_R_W (U403-pin 4) to select whether to read or to write. When the µP is functioning normally, the address and data lines should be toggling at CMOS logic levels. Specifically, the logic high levels should be between 3.1 and 3.3V, and the logic low levels should be between 0 and 0.2V. No other intermediate levels should be observed, and the rise and fall times should be <30ns. The low-order address lines (ADDR 0 - ADDR 7) and the data lines (DATA 0-DATA 7) should be toggling at a high rate, e.g., you should set your oscilloscope sweep to 1us/div. or faster to observe individual pulses. High speed CMOS transitions should also be observed on the µP control lines. On the µP the lines XIRQ (U403-pin 48), MODA LIR (U403-pin 58), MODB VSTPY (U403-pin 57) and RESET (U403-pin 94) should be high at all times during normal operation. Whenever a data or address line becomes open or shorted to an adjacent line, a common symptom is that the RESET line goes low periodically, with the period being in the order of 20ms. In the case of shorted lines you may also detect the line periodically at an intermediate level, i.e. around 2.5V when two shorted lines attempt to drive to opposite rails. The MODA LIR (U403-pin 58) and MODB VSTPY (U403-pin 57) inputs to the µP must be at a logic “1” for it to start executing correctly. After the µP starts execution it will periodically pulse these lines to determine the desired operating mode. While the Central Processing Unit (CPU) is running, MODA LIR is an open-drain CMOS output which goes low whenever the µP begins a new instruction. An instruction typically requires 2-4 external bus cycles, or memory fetches. There are eight analog-to-digital coverter ports (A/D) on U403 labelled within the device block as PEO-PE7. These lines sense the voltage level ranging from 0 to 3.3V of the input line and convert that level to a number ranging from 0 to 255 which is read by the software to take appropriate action. 2-14 5.9 THEORY OF OPERATION Static Random Access Memory (SRAM) The SRAM (U402) contains temporary radio calculations or parameters that can change very frequently, and which are generated and stored by the software during its normal operation. The information is lost when the radio is turned off. The device allows an unlimited number of write cycles. SRAM accesses are indicated by the CS signal U402 (which comes from U403-CSGP2) going low. U402 is commonly referred to as the external RAM as opposed to the internal RAM which is the 3 kilobytes of RAM which is part of the 68HC11FL0. Both RAM spaces serve the purpose. However, the internal RAM is used for the calculated values which are accessed most often. Capacitor C402 and C411 serves to filter out any AC noise which may ride on +3.3 V at U402 6.0 Control Board Audio and Signalling Circuits 6.1 Audio Signalling Filter IC and Compander (ASFIC CMP) The ASFIC CMP (U504) used in the controller has the following four functions: 1. RX/TX audio shaping, i.e. filtering, amplification, attenuation 2. RX/TX signaling, PL/DPL/HST/MDC 3. Squelch detection 4. µP clock signal generation The ASFIC CMP is programmable through the SPI BUS (U504 pins-20/21/22), normally receiving 19 bytes. This programming sets up various paths within the ASFIC CMP to route audio and/or signaling signals through the appropriate filtering, gain and attenuator blocks. The ASFIC CMP also has 6 General Control Bits GCB0-5 which are CMOS level outputs and used for the following: ■ GCBO - BW Select ■ GCBI - switches the audio PA On/Off ■ GCB2 - DC Power On switches the voltage regulator (and the radio) on and off ■ GCB3 - Control on MUX U509 pin 9 to select between Low Cost Mic path to STD Mic Path ■ GCB4 - Control on MUX U509 pin 11 to select between Flat RX path to filtered RX path on the accessory connector. ■ GCB5 - Control on MUX U509 pin 10 to select between Flat TX path mute and Flat TX path Transmit Audio Circuits 7.0 2-15 Transmit Audio Circuits J2 24kOhms U509 15 MIC 46 35 P1 48 2 FLAT TX AUDIO MIC INT GCB3 MIC EXT U509 5 36 TX RTN MUX CONTROL HEAD CONNECTOR EXT MIC 44 TX SND 42 MUX AUX TX ACCESSORY CONNECTOR FILTERS AND PREEMPHASIS MIC ASFIC_CMP IN U504 LIMITER HS SUMMER SPLATTER FILTER LS SUMMER 38 GCB5 FLAT TX AUDIO MUTE VCO ATN ATTENUATOR MOD IN 40 TO RF SECTION (SYNTHESIZER) Figure 2-7 Transmit Audio Paths 7.1 Microphone Input Path The radio supports 2 distinct microphone paths known as internal (from control head J2-15) and external mic (from accessory connector P1-2) and an auxiliary path (FLAT TX AUDIO, from accessory connector P1-5). The microphones used for the radio require a DC biasing voltage provided by a resistive network. The two microphone audio input paths enter the ASFIC CMP at U504-pin 48 (external mic) and U504-pin 46 (internal mic). The microphone is plugged into the radio control head and connected to the audio DC via J2-pin 15. The signal is then routed via C5045 to MUX U509 that select between two paths with different gain to support Low Cost Mic (Mic with out amplifier in it) and Standard Mic. 7.1.1 Low Cost Microphone Hook Pin is shorted to Pin 1(9.3V) inside the Low Cost Mic, This routes 9.3V to R429, and creates 2.6V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 = ‘0’. The audio signal is routed from C5045 via U509-5 (Z0), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int. mic (C5046 100nF creates a 159Hz pole with U504- 46 int mic impedance of 16k ohm). 2-16 7.1.2 THEORY OF OPERATION Standard Microphone Hook Pin is shorted to the hook mic inside the standard Mic, If the mic is out off hook, 3.3V is routed to R429 via R458, D401, and it create 0.7V on MIC_SENSE (u.P U403-67) by Voltage Divider R429/R430. U403 senses this voltage and sends command to ASFIC_CMP U504 to get GCB3 =‘1’. The audio signal is routed from C5045 via U509-3 (Z1), R5072, U507, R5026, C5091, R5014 via C5046 to U504- 46 int mic (C5046 100nF create a159Hz pole with U504- 46 int mic impedance of 16Kohm). 9.3VDC is routed via R5077, R5075 to J2-15, It create 4.65V with Mic Impedance. C5010 supplies AC Ground to create AC impedance of 510 Ohms via R5075. and Filter 9.3V DC mic bias supply. Note: The audio signal at U504-pin 46 should be approximately 12mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The external microphone signal enters the radio on accessory connector P1 pin 2 and is routed via line EXT MIC to R5054. R5078 and R5076 provide the 9.3Vdc bias. Resistive divider R5054/ R5070 divide the input signal by 5.5 and provide input protection for the CMOS amplifier input. R5076 and C5009 provide a 510 ohm AC path to ground that sets the input impedance for the microphone and determines the gain based on the emitter resistor in the microphone’s amplifier circuit. C5047 serves as a DC blocking capacitor. The audio signal at U504-pin 48 should be approximately 14mV for 1.5kHz or 3kHz of deviation with 12.5kHz or 25kHz channel spacing. The FLAT TX AUDIO signal from accessory connector P1-pin 5 is fed to the ASFIC CMP (U504 pin 42 through U509 pin 2 to U509 pin 15 via U506 OP-AMP circuit and C5057. The ASFIC has an internal AGC that can control the gain in the mic audio path. The AGC can be disabled / enabled by the µP. Another feature that can be enabled or disabled in the ASFIC is the VOX. This circuit, along with Capacitor C5023 at U504-pin 7, provides a DC voltage that can allow the µP to detect microphone audio. The ASFIC can also be programmed to route the microphone audio to the speaker for public address operation. 7.2 PTT Sensing and TX Audio Processing Internal microphone PTT is sensed by µP U403 pin 71. Radio transmits when this pin is “0” and selects inside the ASFIC_ CMP U504 internal Mic path. When the internal Mic PTT is “0” then external Mic PTT is grounded via D402. External Mic PTT is sensed by U403 pin 72 via Q412 circuits. The radio transmits when this pin is “0” and selects inside the ASFIC _CMP U504 External Mic path. Inside the ASFIC CMP, the mic audio is filtered to eliminate frequency components outside the 3003000Hz voice band, and pre-emphasized if pre-emphasis is enabled. The signal is then limited to prevent the transmitter from over deviating. The limited mic audio is then routed through a summer, which is used to add in signaling data, and then to a splatter filter to eliminate high frequency spectral components that could be generated by the limiter. The audio is then routed to an attenuator, which is tuned in the factory or the field to set the proper amount of FM deviation. The TX audio emerges from the ASFIC CMP at U504-pin 40 MOD IN, at which point it is routed to the RF section. Transmit Signalling Circuits 8.0 2-17 Transmit Signalling Circuits HS SUMMER 44 MICRO CONTROLLER U403 19 HIGH SPEED CLOCK IN (HSIO) DTMF ENCODER 82 SPI BUS SPLATTER FILTER ASFIC_CMP U504 85 80 5-3-2 STATE ENCODER 18 LOW SPEED CLOCK IN (LSIO) PL ENCODER LS SUMMER ATTENUATOR 40 MOD IN TO RF SECTION (SYNTHESIZER) Figure 2-8 Transmit Signalling Path From a hardware point of view, there are 3 types of signaling: ■ Sub-audible data (PL / DPL / Connect Tone) that gets summed with transmit voice or signaling, ■ DTMF data for telephone communication in trunked and conventional systems, and ■ Audible signaling including MDC and high-speed trunking. Note: All three types are supported by the hardware while the radio software determines which signaling type is available. 8.1 Sub-Audio Data (PL/DPL) Sub-audible data implies signaling whose bandwidth is below 300Hz. PL and DPL waveforms are used for conventional operation and connect tones for trunked voice channel operation. The trunking connect tone is simply a PL tone at a higher deviation level than PL in a conventional system. Although it is referred to as “sub-audible data”, the actual frequency spectrum of these waveforms may be as high as 250 Hz, which is audible to the human ear. However, the radio receiver filters out any audio below 300Hz, so these tones are never heard in the actual system. Only one type of sub-audible data can be generated by U504 (ASFIC CMP) at any one time. The process is as follows, using the SPI BUS, the µP programs the ASFIC CMP to set up the proper lowspeed data deviation and select the PL or DPL filters. The µP then generates a square wave which strobes the ASFIC PL / DPL encode input LSIO U504-pin 18 at twelve times the desired data rate. For example, for a PL frequency of 103Hz, the frequency of the square wave would be 1236Hz. This drives a tone generator inside U504 which generates a staircase approximation to a PL sine wave or DPL data pattern. This internal waveform is then low-pass filtered and summed with voice or data. The resulting summed waveform then appears on U504-pin 40 (MOD IN), where it is sent to the RF board as previously described for transmit audio. A trunking connect tone would be generated in the same manner as a PL tone. 2-18 8.2 THEORY OF OPERATION High Speed Data High speed data refers to the 3600 baud data waveforms, known as Inbound Signaling Words (ISWs) used in a trunking system for high speed communication between the central controller and the radio. To generate an ISW, the µP first programs the ASFIC CMP (U504) to the proper filter and gain settings. It then begins strobing U504-pin 19 (HSIO) with a pulse when the data is supposed to change states. U504’s 5-3-2 State Encoder (which is in a 2-state mode) is then fed to the postlimiter summer block and then the splatter filter. From that point it is routed through the modulation attenuator and then out of the ASFIC CMP to the RF board. MDC is generated in much the same way as trunking ISW. However, in some cases these signals may also pass through a data preemphasis block in the ASFIC CMP. Also these signaling schemes are based on sending a combination of 1200 Hz and 1800 Hz tones only. Microphone audio is muted during high speed data signaling. 8.3 Dual Tone Multiple Frequency (DTMF) Data DTMF data is a dual tone waveform used during phone interconnect operation. It is the same type of tones which are heard when using a “Touch Tone” telephone. There are seven frequencies, with four in the low group (697, 770, 852, 941Hz) and three in the high group (1209, 1336, 1477Hz). The high-group tone is generated by the µP (U403-46) strobing U50419 at six times the tone frequency for tones less than 1440Hz or twice the frequency for tones greater than 1440Hz. The low group tone is generated by the ASFIC CMP, controlled by the µP via SPI bus. Inside U504 the low-group and high-group tones are summed (with the amplitude of the high group tone being approximately 2 dB greater than that of the low group tone) and then preemphasized before being routed to the summer and splatter filter. The DTMF waveform then follows the same path as was described for high-speed data. Receive Audio Circuits 9.0 2-19 Receive Audio Circuits ACCESSORY CONNECTOR 11 1 AUDIO PA U502 9 4 SPKR + 16 SPKR - 1 EXTERNAL SPEAKER 6 INT SPKR+ INT SPKRCONTROL HEAD CONNECTOR 19 MUTE U509 FLT RX AUDIO P1 INTERNAL SPEAKER 20 J2 18 HANDSET AUDIO U505 37 39 10 GCB4 U IO 43 AUX RX 14 41 URX OUT AUDIO GCB1 VOLUME ATTEN. ASFIC_CMP U504 FILTER AND DEEMPHASIS DISC FROM AUDIO RF SECTION (IF IC) 2 DISC PL FILTER LIMITER LIMITER, RECTIFIER FILTER, COMPARATOR LS IO 18 SQUELCH CIRCUIT SQ DET CH ACT 16 17 84 83 MICRO CONTROLLER 80 U403 85 Figure 2-9 Receive Audio Paths 9.1 Squelch Detect The radio’s RF circuits are constantly producing an output at the discriminator (IF IC). This signal (DISC AUDIO) is routed to the ASFIC CMP’s squelch detect circuitry input DISC (U504-pin 2). All of the squelch detect circuitry is contained within the ASFIC CMP. Therefore from a user’s point of view, DISC AUDIO enters the ASFIC CMP, and the ASFIC CMP produces two CMOS logic outputs based on the result. They are CH ACT (U504-16) and SQ DET (U504-17). The squelch signal entering the ASFIC CMP is amplified, filtered, attenuated, and rectified. It is then sent to a comparator to produce an active high signal on CH ACT. A squelch tail circuit is used to produce SQ DET (U504-17) from CH ACT. The state of CH ACT and SQ DET is high (logic “1”) when carrier is detected, otherwise low (logic “0”). CH ACT is routed to the µP pin 84 while SQ DET is routed to the µP pin 83. SQ DET is used to determine all audio mute / unmute decisions except for Conventional Scan. In this case CH ACT is a pre-indicator as it occurs slightly faster than SQ DET. 2-20 9.2 THEORY OF OPERATION Audio Processing and Digital Volume Control The receiver audio signal (DISC AUDIO) enters the controller section from the IF IC where it is.DC coupled to ASFIC CMP via the DISC input U504-pin 2. The signal is then applied to both the audio and the PL/DPL paths The audio path has a programmable amplifier, whose setting is based on the channel bandwidth being received, an LPF filter to remove any frequency components above 3000Hz, and a HPF to strip off any sub-audible data below 300Hz. Next, the recovered audio passes through a deemphasis filter (if it is enabled to compensate for Pre-emphasis which is used to reduce the effects of FM noise). The IC then passes the audio through the 8-bit programmable attenuator whose level is set depending on the value of the volume control. Finally the filtered audio signal passes through an output buffer within the ASFIC CMP. The audio signal exits the ASFIC CMP at AUDIO output (U504 pin 41). The µP programs the attenuator, using the SPI BUS, based on the volume setting. The minimum / maximum settings of the attenuator are set by codeplug parameters. Since sub-audible signaling is summed with voice information on transmit, it must be separated from the voice information before processing. Any sub-audible signaling enters the ASFIC CMP from the IF IC at DISC U504-2. Once inside, it goes through the PL/DPL path. The signal first passes through one of the two low-pass filters, either the PL low-pass filter or the DPL/LST low-pass filter. Either signal is then filtered and goes through a limiter and exits the ASFIC CMP at LSIO (U504-pin 18). At this point, the signal will appear as a square wave version of the sub-audible signal which the radio received. The µP U403 pin 80 will decode the signal directly to determine if it is the tone / code which is currently active on that mode. 9.3 Audio Amplification Speaker (+) Speaker (-) The output of the ASFIC CMP’s digital volume pot, U504-pin 41 is routed through DC blocking capacitor C5049 to the audio PA (U502 pin 1 and 9). The audio power amplifier has one inverted and one non-inverted output that produces the differential audio output SPK+/SPK- (U502 pins 4 and 6) The audio PA is enabled via the ASFIC CMP (U504-GCB1). When the base of Q501 is low, the transistor is off and U502-pin 8 is high, using pull up resistor R5041, and the audio PA is ON. The voltage at U502-pin 8 must be above 8.5Vdc to properly enable the device. If the voltage is between 3.3 and 6.4V, the device will be active but has its input (U502-pins 1/9) off. This is a mute condition which is used to prevent an audio pop when the PA is enabled. The SPK+ and SPK- outputs of the audio PA have a DC bias which varies proportionately with B+ (U502- pin 7). B+ of 11V yields a DC offset of 5V, and B+ of 17V yields a DC offset of 8.5V. If either of these lines is shorted to ground, it is possible that the audio PA will be damaged. SPK+ and SPKare routed to the accessory connector (P1-pin 1 and 16) and to the control head (connector J2-pins 19 and 20). Receive Signalling Circuits 9.4 2-21 Handset Audio Certain handheld accessories have a speaker within them which require a different voltage level than that provided by U502. For these devices HANDSET AUDIO is available at control head connector J2 pin18. The received audio from the output of the ASFIC CMP’s digital volume attenuator is routed to U505 pin 2 where it is amplified. This signal is routed from the output of the op-amp U505 to J2-pin 18. From the control head, the signal is sent directly to the microphone jack. 9.5 Filtered Audio and Flat Audio The ASFIC CMP output audio at U504-pin 39 is filtered and de-emphasized, but has not gone through the digital volume attenuator. From ASFIC CMP U504-pin 39 the signal is routed via R5034 through gate U509-pin 12 and AC coupled to U505-pin 6. The gate controlled by ASFIC CMP port GCB4 selects between the filtered audio signal from the ASFIC CMP pin 39 (URXOUT) or the unfiltered (flat) audio signal from the ASFIC CMP pin 10 (UIO). Resistors R5034 and R5021 determine the gain of op-amp UU505-pin 6 for the filtered audio while R5032 and R5021 determine the gain for the flat Audio. The output of U505-pin 7 is then routed to P1 pin 11 via DC blocking capacitor C5003. Note that any volume adjustment of the signal on this path must be done by the accessory. 10.0 Receive Signalling Circuits DATA FILTER AND DEEMPHASIS DET AUDIO DISCRIMINATOR AUDIO FROM RF SECTION (IF IC) 2 LIMITER HSIO 19 82 44 DISC ASFIC_CMP U504 FILTER LIMITER MICRO CONTROLLER U403 LSIO 18 80 85 PLEAP 8 PLCAP2 25 Figure 2-10 Receive Signalling Paths 10.1 Sub-Audio Data (PL/DPL) and High Speed Data Decoder The ASFIC CMP (U504) is used to filter and limit all received data. The data enters the ASFIC CMP at input DISC (U504 pin 2). Inside U504 the data is filtered according to data type (HS or LS), then it is limited to a 0-3.3V digital level. The MDC and trunking high speed data appear at U504-pin 19, where it connects to the µP U403 pin 82. 2-22 THEORY OF OPERATION The low speed limited data output (PL, DPL, and trunking LS) appears at U504-pin18, where it connects to the µP U403-pin 80. The low speed data is read by the µP at twice the frequency of the sampling waveform; a latch configuration in the ASFIC CMP stores one bit every clock cycle. The external capacitors C5028, and C5026 set the low frequency pole for a zero crossings detector in the limiters for PL and HS data. The hysteresis of these limiters is programmed based on the type of received data. 10.2 Alert Tone Circuits When the software determines that it needs to give the operator an audible feedback (for a good key press, or for a bad key press), or radio status (trunked system busy, phone call, circuit failures), it sends an alert tone to the speaker. It does so by sending SPI BUS data to U504 which sets up the audio path to the speaker for alert tones. The alert tone itself can be generated in one of two ways: internally by the ASFIC CMP, or externally using the µP and the ASFIC CMP. The allowable internal alert tones are 304, 608, 911, and 1823Hz. In this case a code contained within the SPI BUS load to the ASFIC CMP sets up the path and determines the tone frequency, and at what volume level to generate the tone. (It does not have to be related to the voice volume setting.) For external alert tones, the µP can generate any tone within the 100-3000Hz audio band. This is accomplished by the µP generating a square wave which enters the ASFIC CMP at U504 pin 19. Inside the ASFIC CMP this signal is routed to the alert tone generator. The output of the generator is summed into the audio chain just after the RX audio de-emphasis block. Inside U504, the tone is amplified and filtered, then passed through the 8-bit digital volume attenuator, which is typically loaded with a special value for alert tone audio. The tone exits at U504pin 41 and is routed to the audio PA like receive audio. Chapter 3 TROUBLESHOOTING CHARTS This section contains detailed troubleshooting flowcharts. These charts should be used as a guide in determining the problem areas. They are not a substitute for knowledge of circuit operation and astute troubleshooting techniques. It is advisable to refer to the related detailed circuit descriptions in the theory of operation sections prior to troubleshooting a radio. Most troubleshooting charts end up by pointing to an IC to replace. It is not always noted, but it is good practice to verify supplies and grounds to the affected IC and to trace continuity to the malfunctioning signal and related circuitry before replacing any IC. For instance, if a clock signal is not available at a destination, continuity from the source IC should be checked before replacing the source IC. 3-2 1.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2) START Problem in 12 KHz and 25 KHz channel spacing No Yes Go to DC Section 9V on Yes R310 (LNA) OK? No Check RX_EN Go to DC Section No 3V to U301 Okay ? Yes Check Q306, Q300 and U403 Check Q304, D305 and U403 Go to SYN Section Go to DC Section No No RX_EN ON ? Yes LOC_DIST ON? Yes Check LOC_DIST Check TP1 No LO POWER OK ? Yes Check 5V on R336 No 5V Yes (IF AMP) OK ? Check 3V on R338 Go to A Check D301-304 Replace IF Filters( FL304, FL301) If problem in 25 KHz spacing Troubleshooting Flow Chart for Receiver RF (Sheet 1 of 2) 1.1 3-3 Troubleshooting Flow Chart for Receiver (Sheet 2 of 2) From A 3V (IFIC -Vcc) OK ? Go to DC Section No Check the component No Antenna to Mixer circuitry problem No Check visually all receiver components installation ? Yes Installation OK ? Yes Inject - 40dBm (CW) to RF connector Check Power on C332 RF Yes Power > -28 dBM? Check Power on C336 Replace Q305, Q300, U302 Check passive components Replace Q303, Q301 Check passive components No Replace Y301 No Go to DC Section 3V to U301 OK? Yes Y301 OK? No Yes RF Yes Power > -28 dBM? Replace Q302, Y300 Check D301 - 304 Replace U300 Check Y301 44.395 MHz 3-4 2.0 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 45W Transmitter (Sheet 1 of 3) START No or too low power when keyed Check components between Q100 and RF output, Antenna Switch D104, D103, VR102 and Q106 >4A Current increase when keyed? >500mA & <4A <500mA Check PA Stages Yes Control Voltage at TP150 >4Vdc? No Check 9.3V Regulator U501 No Voltage U103 pin 5 = 4.6V? Yes Check power settings, tuning & components between U103 Pin 3 and ASFIC Pin 6 before replacing ASFIC No U103 Pin 3 <1.6Vdc Yes Check U103 Yes Short U100 Pin 3 to ground U100 Pin 3 >1.8Vdc No Check forward Power Sense Circuit Check PA Stages Yes Voltage at TP150 rises? No Check Forward Power Sense Circuit Troubleshooting Flow Chart for 45W Transmitter (Sheet 1 of 3) 2.1 3-5 Troubleshooting Flow Chart for 45W Transmitter (Sheet 2 of 3) Check PA Stages No or too low power when keyed DC Voltage at Q101 base=0? Check Q101, R122, R197, R153, R136, R165, R168, No Yes No DC Voltage at U103 Pin 10=8.9V <2V DC Voltage at U103 Pin 8 >5V Yes Check U103 before replacing U101 2 to 5V DC Voltage at C1095 Check bias tuning before replacing U504 No ASFIC U504 Pin 5 2-3V 0V 2-3V Yes Check components between ASFIC and Q105 before replacing Q105 Check U510 Check Final PA Stages Check resistive network at Pin 9 and 10 of U103 before replacing U101 3-6 2.2 TROUBLESHOOTING CHARTS Troubleshooting Flow Chart for 45W Transmitter (Sheet 3 of 3) Check Final PA Stage Check components between ASFIC & Q100 before replacing Q100 Yes 0V PA_Bias Voltage at R134 Supply Voltage Replace Q100 1-4Vdc RF Voltage after C1044 >100mV? RF Voltage after C1044 >100mV? No Check FGU No Check Bias Tuning before replacing ASFIC U504 Yes Voltage across R122 >2V? No Check components between C1044 & C1117 No Check components between C1117 & Q105 No Check components between Q105 & Q100 Yes RF Voltage Q105 gate >1V? Yes RF Voltage Q100 gate >1.5V? Yes Check components between Q100 & antenna connector Troubleshooting Flow Chart for Synthesizer 3.0 3-7 Troubleshooting Flow Chart for Synthesizer 3V at U200 pins 5, 20, 34 & 36 Start No Check 3V Regulator U508 Yes No Correct Problem Visual check of the Board OK? Yes Yes 5V at pin 6 of D200 No Yes Is U200 Pin 47 = 13VDC? No No +5V at U200 Pins 13 & 30? Is 16.8MHz Signal at U200 Pin 19? No Is 16.8MHz signal at U200 pin 23? Yes Yes Replace U200 No Yes Check Y201 and associated parts Check 5V Regulator U503 Check R228 Is U201 Pin 19 <40 mVDC in RX & >4.5 VDC in TX? (at VCO section) Are signals at Pins 14 & 15 of U200? No Yes Yes Yes Is U200 pin 2 >4.5 VDC in Tx & <40 mVDC in Rx Check D200, D201, C2026, C2025, C2024 & C2027 Yes No Replace U200 No Is there a short between Pin 47 and Pins 14 & 15 of U200? Yes Yes Replace U200 No Are Waveforms at Pins 14 & 15 triangular? No Check R201 No Is RF level at U200 Pin 32 -12 < x <-25 dBm? No If C2052, R208, C2067 C2068. C210, are OK, then see VCO troubleshooting chart Check programming lines between U403 and U200 Pins 7,8 & 9 Remove Shorts No Check µP U403 Troubleshooting Chart Do Pins 7,8 & 9 of U200 toggle when channel is changed? Yes Is information from µP U403 correct? Yes Replace U200 3-8 TROUBLESHOOTING CHARTS 4.0 Troubleshooting Flow Chart for VCO RX VCO Low or no RF Signal at input to PA Low or no RF Signal at TP1 Visual check of board OK? NO Correct Problem NO NO Make sure U508 is working correctly and runner between U508 Pin 1 and U201 Pin 14 & 18 is OK NO Make sure Synthesizer is working correctly and runner between U200 Pin 28 and U201 Pin 3 is OK NO NO Check runner between U200 Pin 2 and U201 Pin 19 NO YES Are Q200 Base at 2.4V Collector at 4.5V Emitter at 1.7V NO 4.8V DC at U201 Pin 19 OK? YES NO If all parts associated with the pins are OK replace U201 Are U201 Pins 13 at 4.4V 15 at 1.1V 10 at 4.5V 16 at 1.9V NO If all parts associated with the pins are OK, replace U201 YES YES If L216, C2071, C2070, Check 9V at R230 NO Is RF available at C2060 YES C2060 are okay replace U201 YES Is RF available at base of Q200 Check Transmiter Pre Driver YES Check parts between TP1 and Q200 4.5V DC at U201 Pin 3 OK? YES YES 35mV DC at U201 Pin 19 OK? 3.3V DC at U201 Pin 14 & 18 OK? YES YES 4.5V DC at U201 Pin 3 OK? Visual check of board OK? YES YES 3.3 DC at U201 Pin 14 & 18 OK? TX VCO NO If all parts from U200 Pin 8 to Base of Q200 are OK, replace U200 Power OK but no modulation NO Audio =180mVrms at “+” side of D205 Replace R212 YES 2.5VDC at D205 YES If R211 is Ok, replace D205 NO Replace R211 Troubleshooting Flow Chart for DC Supply (1 of 2) 5.0 3-9 Troubleshooting Flow Chart for DC Supply (1 of 2) Since the failure of a critical voltage supply might cause the radio to automatically power down, supply voltages should first be probed with a multimeter. If all the board voltages are absent, then the voltage test point should be retested using a rising-edge-triggered oscilloscope. If the voltage is still absent, then another voltage should be tested using the oscilloscope. If that voltage is present, then the original voltage supply in question is defective and requires investigation of associated circuitry. 5V Check VDC on C5006 Go to 3V Replace U503 Yes Yes V=5V ? 9v
Source Exif Data:File Type : PDF File Type Extension : pdf MIME Type : application/pdf PDF Version : 1.6 Linearized : Yes Create Date : 2015:07:26 09:33:12-04:00 Creator : PScript5.dll Version 5.2 Modify Date : 2015:07:26 09:33:12-04:00 Title : XMP Toolkit : Adobe XMP Core 5.4-c005 78.147326, 2012/08/23-13:03:03 Metadata Date : 2015:07:26 09:33:12-04:00 Creator Tool : PScript5.dll Version 5.2 Format : application/pdf Document ID : uuid:b3856c71-6b0f-47e0-a836-43cefafdca8e Instance ID : uuid:5e2f39bc-d4e9-45b0-91f9-9362f1ebaefc Producer : Acrobat Distiller 4.0 for Windows Page Count : 390EXIF Metadata provided by EXIF.tools